Radar system for realizing communication and inductance integration

Abstract

The invention specifically relates to a radar system for realizing communication and inductance integration, and the system comprises a field programmable gate array signal processing assembly which is used for generating an initial local oscillation signal and a customized initial emission waveform according to a control instruction of an upper computer, and outputting the initial emission waveform to an emission assembly, outputting the initial local oscillation signal to a local oscillation system component; the transmitting component is used for modulating a self-defined initial transmitting waveform, then generating a target transmitting signal and transmitting the target transmitting signal; the receiving component is used for receiving the reflected signal and modulating the reflected signal; the local oscillation system component is used for performing frequency conversion processing on the initial local oscillation signal and outputting a first LO signal subjected to up-conversion processing to the transmitting component, so that the transmitting component modulates the first LO signal and a customized initial transmitting waveform; and outputting the second LO signal subjected to down-conversion processing to a receiving component, so that the receiving component modulates the second LO signal and the reflected signal.

Description

Technical Field

[0001] The present invention relates to the field of radar technology, and in particular to a radar system for realizing synaesthesia integration. Background Art

[0002] In the related technology, the millimeter wave radar imaging system mainly relies on the existing monolithic microwave integrated circuit (MMIC) chip. For example, TI's IWR1843, the hardware system of the FMCW millimeter wave radar system is generally composed of three main subsystems: the RF subsystem, the control subsystem and the signal processing subsystem. Among them, the RF subsystem is responsible for generating a radar detection signal of a preset frequency, and then transmitting and receiving the returned reflected signal. The control subsystem is mainly used to perform functions such as configuration, operation control and monitoring of the radar system. The signal processing subsystem is mainly used to transform and process the signals received by the radar. When the signal received by the radar system is converted into a digital signal, it will enter the signal processing subsystem to complete a more complex algorithm flow calculation. For millimeter-wave radar platforms, the generation of local oscillator signals is a key technical link. Traditional phase-locked loop (PLL) technology is widely used in the generation of local oscillator signals, but it has some limitations, especially in the scenario of interaesthesia modulation, these limitations are particularly obvious; for example: 1) the signal bandwidth generated by the phase-locked loop is relatively narrow; 2) the frequency conversion time of the phase-locked loop is relatively long; 3) the frequency resolution of the phase-locked loop is relatively low; 4) the output waveform generated by the phase-locked loop is not flexible enough. This makes the millimeter-wave radar platform have certain technical defects for the application of interaesthesia integration; for example, from the perspective of signal transmission, the transmission waveform is mainly a single frequency-modulated continuous wave, and the transmission waveform supports low degrees of freedom; and the local oscillator signal frequency agility brought by the phase-locked loop is insufficient, which also makes the demodulation information corresponding to the received signal require more complex algorithms to implement.

[0003] It should be noted that the information disclosed in the above background technology section is only used to enhance the understanding of the background of the present invention, and therefore may include information that does not constitute the prior art known to ordinary technicians in the field. Summary of the invention

[0004] The present invention provides a radar system for realizing synaesthesia integration, which can effectively overcome the defects existing in the prior art.

[0005] Other features and advantages of the present invention will become apparent from the following detailed description, or may be learned in part by practice of the present invention.

[0006] According to a first aspect of the present invention, there is provided a radar system for realizing synaesthesia integration, comprising:

[0007] A field programmable gate array signal processing component is used to generate an initial local oscillation signal and a customized initial transmission waveform according to a control instruction of a host computer, and output the initial transmission waveform to a transmission component, and output the initial local oscillation signal to a local oscillator system component;

[0008] A transmitting component, used to generate a target transmitting signal after modulating a user-defined initial transmitting waveform and transmitting the target transmitting signal;

[0009] A receiving component, used for receiving a reflected signal and modulating the reflected signal;

[0010] The local oscillator system component is used to perform frequency conversion processing on the initial local oscillation signal, and output the first LO signal after up-conversion processing to the transmitting component, so that the transmitting component can modulate the first LO signal and the customized initial transmission waveform; and output the second LO signal after down-conversion processing to the receiving component, so that the receiving component can modulate the second LO signal and the reflected signal.

[0011] In some exemplary embodiments, the transmitting component includes a digital-to-analog converter module, a low-pass filter, a first mixer, a first broadband amplifier, and a transmitting antenna connected in sequence;

[0012] The receiving component includes an analog-to-digital converter module, a low-pass filter, a second mixer, a second broadband amplifier, and a receiving antenna which are connected in sequence.

[0013] In some exemplary embodiments, the local oscillator system includes: a baseband direct digital frequency synthesis module, a mixing module;

[0014] Wherein, the baseband direct digital frequency synthesis module is used to output a carrier frequency broadband signal and a carrier frequency clock to the mixing module;

[0015] The mixing module is used to mix the carrier bandwidth signal and the carrier clock signal to output a target bandwidth signal.

[0016] In some exemplary embodiments, the baseband direct digital frequency synthesis module includes a digital-to-analog converter, a balun device, an oven-controlled crystal oscillator, and a clock distribution device;

[0017] The digital-to-analog converter is used to convert the bandwidth signal generated in the baseband signal board into an analog signal and output it to the balun device;

[0018] The balun device is used to perform signal balance conversion on the analog signal generated by the digital-to-analog converter and then output it to the mixing module;

[0019] The clock distribution device is connected to the constant temperature crystal oscillator, the mixing module, and the digital-to-analog converter respectively, and is used to divide the clock generated by the constant temperature crystal oscillator, generate a reference clock and output it to the digital-to-analog converter, and generate a carrier frequency clock and output it to the mixing module.

[0020] In some exemplary embodiments, the mixing module includes a first filter, a first attenuator, a second filter, a mixer, a third filter, a first amplifier, a second attenuator, and a second amplifier connected in sequence; the mixer is also connected in sequence to a third amplifier and a fourth filter;

[0021] Among them, the first filter is used to filter out near-end spurious signals; the second filter is used to filter out DAC image frequency and clock frequency; the third filter is used to suppress out-of-band signals; the fourth filter and the third amplifier are used to filter and amplify the carrier clock signal.

[0022] In some exemplary embodiments, the first broadband amplifier includes a bandpass filter, a variable gain amplifier, a radio frequency power amplifier, and a bandpass filter connected in sequence;

[0023] The second broadband amplifier includes a bandpass filter, a variable gain amplifier, a low noise power amplifier, and a bandpass filter which are connected in sequence.

[0024] In some exemplary embodiments, the field programmable gate array signal processing component includes:

[0025] The processing system part is used to respond to the control analysis of the host computer to generate the baseband signal waveform defined by the mode, control the opening and closing time of the pulse signal, process the radar signal after data acquisition, and upload the point cloud data after imaging to the host computer;

[0026] The programmable logic part is used to analyze the pulse parameters to generate a pulse periodic signal, and output the baseband signal and the local oscillator signal to the digital-to-analog converter module of the transmitting component and the baseband direct digital frequency synthesis module of the local oscillator system component according to the pulse periodic signal; at the same time, the analog-to-digital converter module of the receiving component is demodulated and preprocessed in radar signal processing.

[0027] The radar system provided by the embodiment of the present invention can support the generation of arbitrary user-defined waveforms in the digital part by setting a field programmable gate array signal processing component, and supports more transmission waveforms. In addition, the field programmable gate array signal processing component can be used to realize the demodulation function, increase the modulation baseband waveform, and realize the hardware platform with the function of synaesthesia integration. In addition, by setting the local oscillator system component, the direct digital frequency synthesis module can be used to replace the phase-locked loop to generate the local oscillator signal, which greatly improves the effect of frequency agility and has good feedback in the application of synaesthesia integration.

[0028] It is to be understood that the foregoing general description and the following detailed description are exemplary and explanatory only and are not restrictive of the invention. BRIEF DESCRIPTION OF THE DRAWINGS

[0029] The accompanying drawings herein are incorporated into and constitute a part of the specification, illustrate embodiments consistent with the present invention, and together with the specification are used to explain the principles of the present invention. Obviously, the accompanying drawings described below are only some embodiments of the present invention, and for those of ordinary skill in the art, other accompanying drawings can be obtained based on these accompanying drawings without creative work.

[0030] Figure 1 A schematic diagram schematically illustrates a radar system for realizing synaesthesia integration according to an exemplary embodiment of the present invention;

[0031] Figure 2 A schematic diagram schematically illustrates an antenna structure according to an exemplary embodiment of the present invention;

[0032] Figure 3 A schematic diagram schematically illustrates a local oscillator system in an exemplary embodiment of the present invention;

[0033] Figure 4 A schematic diagram of a radar system according to an exemplary embodiment of the present invention is schematically shown. DETAILED DESCRIPTION

[0034] Example embodiments will now be described more fully with reference to the accompanying drawings. However, example embodiments can be implemented in many forms and should not be construed as limited to the examples set forth herein; rather, these embodiments are provided so that the present invention will be more comprehensive and complete and fully convey the concepts of the example embodiments to those skilled in the art. The described features, structures, or characteristics may be combined in any suitable manner in one or more embodiments.

[0035] In addition, the accompanying drawings are only schematic illustrations of the present invention and are not necessarily drawn to scale. The same reference numerals in the figures represent the same or similar parts, and their repeated description will be omitted. Some of the block diagrams shown in the accompanying drawings are functional entities and do not necessarily correspond to physically or logically independent entities. These functional entities can be implemented in software form, or implemented in one or more hardware modules or integrated circuits, or implemented in different networks and / or processor devices and / or microcontroller devices.

[0036] In related technologies, most millimeter-wave radar platforms only consider the specific application of radar, but do not combine it with communication information. In traditional millimeter-wave radar platforms, the realization of communication functions mainly depends on the modulation function, and the realization of modulation functions mainly relies on the hardware implementation of phase shifters and frequency modulators. Traditional millimeter-wave radars usually use phase shifters to change the phase of the transmitted signal to achieve beam control and anti-interference capabilities. This hardware implementation method requires precise control and calibration, which increases the difficulty of system design and debugging and is costly. Moreover, the achievable modulation coding is very limited, and the flexibility and reconfigurability requirements for the implementation of Integrated Sensing And Communication (ISAC) cannot be met.

[0037] In view of the shortcomings and deficiencies of the prior art, a radar system is provided in this example implementation.

[0038] The radar system for realizing synaesthesia integration in this example implementation will be described in more detail below in conjunction with the accompanying drawings and embodiments.

[0039] refer to Figure 1 As shown, the radar system for realizing interawareness integration includes: a field programmable gate array (FPGA) signal processing component 11, a transmitting component 12, a receiving component 13, and a local oscillator system component 14. Among them, the FPGA signal processing component 11 can be used to generate an initial local oscillation signal and a customized initial transmission waveform according to the control instruction of the host computer, and output the initial transmission waveform to the transmitting component, and output the initial local oscillation signal to the local oscillator system component. The transmitting component 12 can be used to modulate the customized initial transmission waveform to generate a target transmission signal and transmit the target transmission signal. The receiving component 13 can be used to receive the reflected signal and modulate the reflected signal. The local oscillator system component 14 can be used to perform frequency conversion processing on the initial local oscillation signal, and output the first LO signal after up-conversion processing to the transmitting component, so that the transmitting component can modulate the first LO signal and the customized initial transmission waveform; and output the second LO signal after down-conversion processing to the receiving component, so that the receiving component can modulate the second LO signal and the reflected signal.

[0040] Exemplary, reference Figure 1As shown, the transmitting component 12 includes a digital-to-analog converter (DAC) module 121, a low-pass filter (LPF) 122, a first mixer 123, a first broadband amplifier, and a transmitting antenna 124, which are connected in sequence. Among them, the first broadband amplifier includes a bandpass filter (BPF) 125, a variable gain amplifier (VGA) 126, a radio frequency power amplifier (PA) 127, and a bandpass filter 128, which are connected in sequence.

[0041] Exemplarily, the receiving component 13 includes an analog-to-digital converter module 131, a low-pass filter 132, a second mixer 133, a second broadband amplifier, and a receiving antenna 134, which are connected in sequence. The second broadband amplifier includes a bandpass filter 135, a variable gain amplifier 136, a low noise power amplifier (Low Noise Amplifier, LNA) 137, and a bandpass filter 138, which are connected in sequence.

[0042] Specifically, the RF front end consists of a transceiver antenna, a receiving link, and a transmitting link. The transmitting link input is mainly provided by the local oscillator system, which provides a local oscillator (LO) signal as the modulated input and a baseband DAC signal as the modulating input. The LO signal is input to each RF chip through the SMP (SubMiniaturePconnector) connector, and the baseband signal is input to each RF chip through the FMC connector (FPGA Mezzanine Card). The SMP connector is a small radio frequency (RF) connector used for signal transmission in high-frequency applications and microwave communication systems, and can be easily plugged in and out quickly. Reference Figure 2 As shown in the figure, the RF front-end system structure is based on 4T4R sparse antenna, which greatly simplifies the antenna layout design process in terms of antenna scale, and the antenna layout requirements are different in different scenarios. In addition, the antenna can be a microstrip series-fed antenna.

[0043] Specifically, an upconverter 142, a variable gain amplifier VGA126, a bandpass filter (125, 128), and a radio frequency power amplifier PA127 may be provided in the transmission link. Among them, the first-stage module is used to realize the upconversion function of the LO signal; the upconverter 142 may be a 6-times multiplier, which allows the use of a lower frequency range of LO input signals between 11.8 GHz and 12.7 GHz. The LO path feeds an orthogonal divider 129, which then drives the on-chip balancer of the I and Q mixer 123 core; the RF outputs of the I and Q mixers are then summed by the on-chip power synthesizer and then fed to the second-stage module. The VGA1 in the second-stage module uses multiple gain stages and interleaved voltage variable attenuation stages to form a low-noise, high-linearity variable gain amplifier to achieve secondary amplification of the signal, which is then fed to the third-stage module. The third-stage module may include a power amplifier, which uses multiple cascaded gain stages to form an amplifier and is connected to the transmitting antenna through a circulator. The bandpass filters (125, 128) are used to filter out harmonics and spurious signals caused by devices and the like and to suppress other out-of-band signals.

[0044] Specifically, the receiving chain may include a down converter 143, a low noise power amplifier 137, and a bandpass filter (135, 138). Among them, the first stage module is a low noise power amplifier, which is mainly used to low-noise amplify the echo signal received by the receiving antenna and then feed it to the second stage module. The second stage module may include an I / Q down converter 143 with an integrated LO buffer and a 6x multiplier. The 6x multiplier allows the use of LO input signals in a lower frequency range, typically between 11.5GHz and 13GHz. The LO path feeds an orthogonal divider 139, followed by an on-chip balancer that drives the I and Q mixer cores. Then, the RF input of the I and Q mixer 133 is driven by an on-chip power divider, and finally the down-converted signal is fed to the intermediate frequency output. The bandpass filter (135, 138) is used to filter out interference signals in the reflected signal received by the receiving antenna.

[0045] Exemplary, reference Figure 3 As shown, the local oscillator system includes: a baseband direct digital frequency synthesis (Direct Digital Synthesizer, DDS) module 31, and a mixing module 32; wherein the baseband DDS module is used to output a carrier frequency broadband signal and a carrier frequency clock to the mixing module 31; the mixing module 32 is used to mix the carrier frequency broadband signal and the carrier frequency clock signal and output the target bandwidth signal.

[0046] Exemplarily, the baseband DDS module 31 includes: a digital-to-analog converter 311, a balun device 312, a constant temperature crystal oscillator 313, and a clock distribution device 314. The digital-to-analog converter 311 is used to convert the bandwidth signal generated by the baseband signal board clock into an analog signal, and output it to the balun device 312. The balun device 312 is used to perform signal balance conversion on the analog signal generated by the digital-to-analog converter and output it to the mixing module 32. The clock distribution device 314 is respectively connected to the constant temperature crystal oscillator 313, the mixing module 32, and the digital-to-analog converter 311, and is used to perform frequency division processing on the clock generated by the constant temperature crystal oscillator, generate a reference clock and output it to the digital-to-analog converter, and generate a carrier frequency clock and output it to the mixing module.

[0047] Exemplarily, the mixing module 32 includes a first filter 321, a first attenuator 322, a second filter 323, a mixer 324, a third filter 325, a first amplifier 326, a second attenuator 327, and a second amplifier 328 connected in sequence; the mixer 324 is also connected in sequence to a third amplifier 332 and a fourth filter 331. The first filter is used to filter out near-end spurious signals; the second filter is used to filter out DAC image frequency and clock frequency; the third filter is used to suppress out-of-band signals; and the fourth filter and the third amplifier are used to filter and amplify the carrier frequency clock signal.

[0048] Specifically, the input of the mixing module 32 may include a high-quality carrier clock signal and a baseband bandwidth signal, and the output is a mixed broadband signal. The working process of the mixing module may include the following steps:

[0049] Step 1). The clock is generated by the constant temperature crystal oscillator in the baseband signal board, and is divided by the clock frequency divider. One channel is output to the digital-to-analog converter to provide a reference clock, and the other channel is output to the mixing module as a carrier clock. In addition, the two output frequencies are different.

[0050] Step 2). The baseband signal board generates a broadband signal and outputs it to the digital-to-analog converter, which converts the digital signal into an analog level and outputs it to the mixing module as a carrier broadband signal.

[0051] Step 3). In the mixing module, filtering is first performed to filter out other non-related signals such as spurious and harmonic waves. Secondly, considering the power matching and impedance matching between modules at each level, corresponding amplifiers and attenuators are required, and then the mixing output is performed in the mixer. After mixing, a broadband signal within the specified band is obtained, and then a bandpass filter is used to suppress the out-of-band signal; then the broadband signal that meets the frequency and power requirements is obtained through the amplifier and attenuator.

[0052] Exemplarily, the field programmable gate array signal processing component 11 includes: a processing system part PS (Processor System) 51 and a programmable logic part PL (Programmable Logic) 52. Among them, the processing system part 51 can be used to respond to the control analysis of the host computer to generate the baseband signal waveform defined by the mode, and control the pulse signal opening and closing time, perform radar signal processing operations after data acquisition, and upload the point cloud data after imaging to the host computer. Among them, the processing system part 51 is mainly used to realize the functions of parameter configuration, data interaction cache, data signal processing, and data upload; the baseband signal waveform can be a customized initial transmission waveform, and the pulse repetition time parameter can also be configured according to the mode word configured by the host computer. The programmable logic part 52 can be used to analyze the pulse parameters to generate a pulse period signal, and output the baseband signal and the local oscillator signal to the digital-to-analog converter module of the transmitting component and the baseband direct digital frequency synthesis module of the local oscillator system component according to the pulse period signal; at the same time, the analog-to-digital converter module of the receiving component is demodulated and preprocessed in radar signal processing. Among them, the programmable logic part 52 is mainly used to realize the functions of waveform distribution, data acquisition synchronization, data preprocessing, and data interaction.

[0053] Specifically, refer to Figure 4 As shown, the FPGA signal processing component mainly realizes the generation of arbitrary broadband signals, the modulation of the required baseband signals, and the acquisition of original echo data, data demodulation, data preprocessing, radar imaging and other operations.

[0054] Specifically, the initialization process may include:

[0055] Step a1), initialize the clock and reset of each chip and module. Specifically, the 100MHz clock generated by the constant temperature crystal oscillator is used as the reference clock of the clock chip. After the clock chip is divided, it is output to the logic master clock of the FPGA chip; the rest is mainly used for the working clock of the ADC module and DAC module, the reference clock of the GTX device, etc. The ADC module clock is set to 350MHz (upper and lower edge sampling), and the FPGA reference clock is 50Mhz. The reference clock of GTX is set to 156.25MHz. A system reset module is generated inside the FPGA, which is used to asynchronously reset and synchronously release the sub-modules before initialization is completed.

[0056] Step a2), configure the DAC module, DDS module, and ADC data acquisition module. Specifically, the FPGA chip configures the digital-to-analog converter chip through the serial peripheral interface protocol. The order of register configuration is as follows:

[0057] 1) Perform reset release, enable TX_ENA level, and enable reset state;

[0058] 2) Configure available registers;

[0059] 3) Synchronous FIFO configuration, synchronous clock divider, providing intra-chip and inter-chip synchronization signals;

[0060] 4) Provide fixed test words for testing LVDS and dynamically adjust IOdleay value;

[0061] 5) After determining the delay value, switch to normal data mode.

[0062] The specific workflow of the radar system may include:

[0063] Step S1, first initialize each clock chip and reset the data link of the whole machine.

[0064] Step S2, the host computer is connected to the PHY Ethernet port of the baseband signal board through a network cable, and four baseband waveforms with different frequency, phase and amplitude are generated through command words, so as to use different frequencies as the form of this modulation.

[0065] Step S3, the PS part receives the configuration mode word from the host computer, generates waveforms according to the mode word protocol, and updates the parameters of the PRT signal (e.g., number of pulses, pulse high level duration, low level duration), etc.; for example, it generates 10MHz, 20MHz, 30MHz, 40MHz baseband periodic waveforms, [-400, 400]MHz broadband waveforms. The PS part moves 1024 PRT signals of 40us high level and 5us low level to different BRAM (Block RAM) cores of the PL part through DMA (Direct Memory Access).

[0066] In step S4, the PS part receives the scanning mode word from the host computer, and notifies the PL part to generate a PRT (Pulse repetition time) signal through a GPIO (General-Purpose Input / Output) signal. The state machine is turned on according to the PRT signal to read data from the BRAM, convert it into different data protocol formats and send it to the DAC device and the DDS device, convert the digital signal into an analog signal, and then output it through operations such as mixing, filtering, amplification, and frequency doubling by the RF chip at the front end of the transmitter.

[0067] Step S5, the electromagnetic wave signal is transmitted, and the echo signal reflected by the target is down-converted by the receiver RF chip to obtain a baseband signal, which is converted into a digital signal by the ADC. Under the PRT synchronization operation, the ADC data is intercepted to obtain the difference frequency signal reflected by the actual target, and data demodulation and correction preprocessing are performed on it.

[0068] Step S6: The data can be directly uploaded to the host computer through the GTX-10GE interface or the GTX-40GE interface for offline processing, or the data can be moved to the PS through the DMA device. The 4D imaging algorithm is implemented in the PS, and the processed point cloud data is obtained and sent to the host computer in the corresponding protocol format for point cloud display.

[0069] For example, OFDM signals can be used as waveforms for 4G / 5G wireless communications. They have the advantages of high spectrum efficiency, effective resistance to multipath effects, flexible subcarrier modulation, easy implementation, and broadband synthesizable characteristics, and can be applied to integrated waveform design. Specifically, 1) broadband frequency signals and baseband OFDM coding can be generated through the DDS frequency generator IP core of FPGA; 2) data can be pre-stored in BRAM resources, and synchronous scanning can be turned on through display control, and data can be forwarded to the local oscillator output and baseband output through the high-speed interface protocol; 3) the baseband signal can be modulated to different subcarrier groups through the RF chip. Since the subcarriers of OFDM signals are orthogonal, the signals on different subcarrier groups naturally meet the orthogonality, so they can be separated at the transmitting and receiving ends. 4) ADC echo data is collected through the target scene, and the demodulation function is realized inside the FPGA; 5) data demodulation is performed, and radar data is processed for radar imaging, which is usually achieved by performing distance and Doppler FFT, then using CFAR for non-coherent detection, and finally using spatial FFT to estimate the angle. After obtaining the point cloud data, higher-level algorithms can be used to post-process the point cloud data, such as clustering, tracking, and classification, to represent real-world targets; communication data is restored to communication information, usually using time-frequency domain synchronization, channel estimation, equalization, and descrambling operations.

[0070] The radar system provided by the present invention can realize a millimeter-wave 4D radar platform based on synaesthesia integration. The overall system architecture can be divided into a radio frequency part, a local oscillator part, and a baseband processing part. The radio frequency part uses ADMV7410 devices and ADMV7310 devices plus a microstrip antenna. The local oscillator part mainly adopts a mixer and filter design, and the baseband part mainly adopts FPGA plus peripheral devices; the peripheral devices include DAC, DDS and ADC, as well as clock chips, etc. This solution increases the baseband signal output, so that modulation in the radio frequency part increases the flexibility and functionality of the system transmission. Using a direct digital frequency synthesizer instead of a phase-locked loop to generate an up-conversion signal improves the stability and accuracy of the signal. At the data processing end, data demodulation and data post-processing are performed through FPGA, and imaging data and mode control are displayed with the host computer software part.

[0071] Compared with traditional millimeter-wave radars, the present invention considers the inherent defects existing in the prior art from the perspective of hardware (for example, the common technical solutions use ARM or DSP to uniformly generate and control the frequency-modulated continuous wave output, which simplifies the operation, but it brings about a waste of time domain and frequency domain resources, and the imaging requirements of existing communication millimeter-wave radars are often not met); the present invention starts from the characteristics of interawareness integration, waveform integration design, and builds a set of 4D millimeter-wave platforms, and selects a transceiver RF chip that can support modulation from the radio frequency system. From the traditional millimeter-wave platform that only supports a single frequency-modulated continuous wave, the baseband waveform output is added to realize the local oscillator waveform of arbitrary modulation. From the single-chip millimeter-wave platform, TI's AWR 2243 platform is used as the background to compare the support of the present invention for different transmission waveforms. The platform support comparison under different radar waveform systems is shown in Table 1. It can be seen that it has good support for various existing transmission systems and coding waveforms, so it is more flexible and convenient from the perspective of software algorithm verification.

[0072] Table 1

[0073]

[0074]

[0075] The present invention designs a hardware system based on devices such as FPGA+ADC+DAC. Compared with traditional millimeter-wave radar, the transmission scanning time is compressed, and on this basis, false targets are avoided while improving energy utilization. Simulation shows that this method improves the performance of radar detection and imaging without affecting communication performance.

[0076] In general, mainly from the combination with existing theoretical needs, on the one hand, the system provides higher degree of freedom waveform design modulation, supports more complex theoretical algorithm research, on the other hand, the system has high integration, and only needs to change the software program in the later stage to complete the conversion of coded communication radar or continuous wave radar, which can meet the needs of different parameter radars in different situations. At the same time, the correction link solves the problem of poor consistency of local oscillator mixing amplitude and phase between different chips caused by the device, and meets the requirements of amplitude and phase consistency of broadband signals in existing radars.

[0077] This solution uses a chip that modulates and outputs the baseband and local oscillator inputs. According to the requirements of the integrated waveform design, it is possible to realize the local oscillator signal carrier to different subcarriers. An integrated configurable RF chip can also be used, which can also replace this modulation method. In addition, in the transmission link, the local oscillator signal adopts a multi-stage carrier frequency amplification form, and the local oscillator signal or other direct frequency synthesizer can be freely output through the internal integration of a custom chip to generate the target signal. In this solution, mainly based on FPGA as the main control chip, a synaesthesia integrated 4D millimeter wave radar with a feasible solution is built. Other devices can be used to replace FPGA devices in the signal processing control device, but the signal processing operation amount and real-time performance and the versatility between interfaces should be considered to ensure the stability between data streams and the real-time performance of data post-processing. Similarly, the system design method is not limited to small-scale systems, but also applies to large-scale MIMO arrays. The present invention is not only suitable for assisted driving of vehicle-mounted radars, but can also be applied to security radars in scenes such as airports and subways. Relying on the highly flexible frequency synthesis characteristics, the present invention is also suitable for scenes such as indoor personnel detection, breathing and heartbeat extraction of life features. It mainly depends on the specific radar parameters of the millimeter-wave radar transmission and reception links, providing a wide range of application possibilities.

[0078] Other embodiments of the invention will readily occur to those skilled in the art after considering the specification and practicing the invention herein. This application is intended to cover any variations, uses, or adaptations of the invention that follow the general principles of the invention and include common knowledge or customary techniques in the art that are not disclosed by the present invention. The specification and examples are to be considered exemplary only, and the true scope and spirit of the invention are indicated by the claims.

[0079] It should be understood that the present invention is not limited to the exact construction that has been described above and shown in the drawings and that various modifications and changes may be made without departing from the scope thereof. The scope of the present invention is limited only by the appended claims.

Claims

1. A radar system for realizing synaesthesia integration, characterized in that: The system comprises: A field programmable gate array signal processing component is used to generate an initial local oscillation signal and a customized initial transmission waveform according to a control instruction of a host computer, and output the initial transmission waveform to a transmission component, and output the initial local oscillation signal to a local oscillator system component; A transmitting component, used to generate a target transmitting signal after modulating a user-defined initial transmitting waveform and transmitting the target transmitting signal; A receiving component, used for receiving a reflected signal and modulating the reflected signal; The local oscillator system component is used to perform frequency conversion processing on the initial local oscillation signal, and output the first LO signal after up-conversion processing to the transmitting component, so that the transmitting component can modulate the first LO signal and the customized initial transmission waveform; and output the second LO signal after down-conversion processing to the receiving component, so that the receiving component can modulate the second LO signal and the reflected signal.

2. The radar system according to claim 1, characterized in that The transmitting component includes a digital-to-analog converter module, a low-pass filter, a first mixer, a first broadband amplifier, and a transmitting antenna connected in sequence; The receiving component includes an analog-to-digital converter module, a low-pass filter, a second mixer, a second broadband amplifier, and a receiving antenna which are connected in sequence.

3. The radar system according to claim 2, characterized in that The first broadband amplifier includes a bandpass filter, a variable gain amplifier, a radio frequency power amplifier, and a bandpass filter connected in sequence; The second broadband amplifier includes a bandpass filter, a variable gain amplifier, a low noise power amplifier, and a bandpass filter which are connected in sequence.

4. The radar system according to claim 1 or 2, characterized in that: The local oscillator system comprises: a baseband direct digital frequency synthesis module and a mixing module; Wherein, the baseband direct digital frequency synthesis module is used to output a carrier frequency broadband signal and a carrier frequency clock to the mixing module; The mixing module is used to mix the carrier bandwidth signal and the carrier clock signal to output a target bandwidth signal.

5. The radar system according to claim 4, characterized in that The baseband direct digital frequency synthesis module includes a digital-to-analog converter, a balun device, a constant temperature crystal oscillator, and a clock distribution device; The digital-to-analog converter is used to convert the bandwidth signal generated in the baseband signal board into an analog signal and output it to the balun device; The balun device is used to perform signal balance conversion on the analog signal generated by the digital-to-analog converter and then output it to the mixing module; The clock distribution device is connected to the constant temperature crystal oscillator, the mixing module, and the digital-to-analog converter respectively, and is used to divide the clock generated by the constant temperature crystal oscillator, generate a reference clock and output it to the digital-to-analog converter, and generate a carrier frequency clock and output it to the mixing module.

6. The radar system according to claim 4, characterized in that The mixing module comprises a first filter, a first attenuator, a second filter, a mixer, a third filter, a first amplifier, a second attenuator, and a second amplifier connected in sequence; the mixer is also connected in sequence to a third amplifier and a fourth filter; Among them, the first filter is used to filter out near-end spurious signals; the second filter is used to filter out DAC image frequency and clock frequency; the third filter is used to suppress out-of-band signals; the fourth filter and the third amplifier are used to filter and amplify the carrier clock signal.

7. The radar system according to claim 1, characterized in that The field programmable gate array signal processing component comprises: The processing system part is used to respond to the control analysis of the host computer to generate the baseband signal waveform defined by the mode, control the opening and closing time of the pulse signal, process the radar signal after data acquisition, and upload the point cloud data after imaging to the host computer; The programmable logic part is used to analyze the pulse parameters to generate a pulse periodic signal, and output the baseband signal and the local oscillator signal to the digital-to-analog converter module of the transmitting component and the baseband direct digital frequency synthesis module of the local oscillator system component according to the pulse periodic signal; at the same time, the analog-to-digital converter module of the receiving component is demodulated and preprocessed in radar signal processing.

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