Phase-shifted metasurface structure, radio interface phase shifter and antenna device

Abstract

The application provides a phase shift super surface structure, an air interface phase shifter and an antenna device, and can solve the problems of complex system, poor flexibility and poor regulation precision. The phase shift super surface structure comprises at least two oscillators parallel to each other, and the lengths of at least part of the oscillators are different; at least one oscillator is provided with at least one tuning device, and the tuning device is used for adjusting the electrical size of the oscillator.

Description

TECHNICAL FIELD

[0001] The present disclosure relates to the field of communication technology, in particular to a phase-shifting metasurface structure, an air interface phase shifter and an antenna device. BACKGROUND

[0002] In a wireless communication system, antenna technology is one of the key areas to improve the performance of the communication system. With the increasing application demand of 5G and future 6G communication systems, the importance of antenna array beamforming and pointing control is increasingly prominent. As the core component of phased array antennas, phase shifters undertake the task of regulating the radiation phase of antenna elements, and are the key to realizing the flexibility and dynamic performance of phased array antennas.

[0003] In application scenarios that require simultaneous control of two orthogonal polarized signals, the prior art needs to use two independent phase shifters to process different polarized signals. This not only increases the system complexity, but also reduces the flexibility and control accuracy of the system. SUMMARY

[0004] The present disclosure provides an air interface phase shifter and an antenna device, which can solve the problems of system complexity, poor flexibility and control accuracy in the prior art.

[0005] In a first aspect, the embodiments of the present disclosure provide a phase-shifting metasurface structure, comprising at least two oscillators parallel to each other, and the lengths of at least part of the oscillators are different; at least one of the oscillators is provided with at least one tuning device, and the tuning device is used to adjust the electrical size of the oscillator.

[0006] In a second aspect, the embodiments of the present disclosure provide a phase-shifting metasurface structure, comprising a first closed body connected at the head and tail and a second closed body connected at the head and tail, the first closed body and the second closed body are arranged in the same layer or different layers; the first closed body and the second closed body have the same shape and different sizes; at least one of the first closed body and the second closed body is provided with at least one tuning device, and the tuning device is used to adjust the electrical size of the closed body.

[0007] In a third aspect, the embodiments of the present disclosure further provide an air interface phase shifter, comprising: the above phase-shifting metasurface structure provided by the embodiments of the present disclosure.

[0008] In a fourth aspect, the embodiments of the present disclosure further provide an antenna device, comprising: the above air interface phase shifter provided by the embodiments of the present disclosure; a radiating antenna cascaded with the air interface phase shifter. BRIEF DESCRIPTION OF DRAWINGS

[0009] In the drawings of the embodiments of the present disclosure:

[0010] Figure 1 The first structure diagram of the phase-shifting metasurface structure provided by an embodiment of the present disclosure;

[0011] Figure 2 A second structural diagram of the phase-shifting metasurface structure provided by an embodiment of the present disclosure;

[0012] Figure 3 A third structural diagram of the phase-shifting metasurface structure provided by an embodiment of the present disclosure;

[0013] Figure 4 A fourth structural diagram of the phase-shifting metasurface structure provided by an embodiment of the present disclosure;

[0014] Figure 5 A fifth structural diagram of the phase-shifting metasurface structure provided by an embodiment of the present disclosure;

[0015] Figure 6 A sixth structural diagram of the phase-shifting metasurface structure provided by an embodiment of the present disclosure;

[0016] Figure 7 A seventh structural diagram of the phase-shifting metasurface structure provided by an embodiment of the present disclosure;

[0017] Figure 8 A curve diagram about the radiation phase and the capacitance value of the varactor;

[0018] Figure 9 A first structural diagram of the phase-shifting metasurface structure provided by another embodiment of the present disclosure;

[0019] Figure 10 A second structural diagram of the phase-shifting metasurface structure provided by another embodiment of the present disclosure;

[0020] Figure 11 A structural diagram of the air interface phase shifter provided by an embodiment of the present disclosure;

[0021] Figure 12 A structural diagram of the air interface phase shifter provided by an embodiment of the present disclosure; Figure 11 A structural diagram of the first phase-shifting metasurface structure and the second phase-shifting metasurface structure in FIG. 5;

[0022] Figure 13 Another structural diagram of the air interface phase shifter provided by an embodiment of the present disclosure;

[0023] Figure 14 A structural diagram of the antenna device provided by an embodiment of the present disclosure;

[0024] Figure 15 A structural diagram of the antenna device provided by an embodiment of the present disclosure;

[0025] Figure 16 Another structural diagram of the antenna device provided by an embodiment of the present disclosure;

[0026] Figure 17 Fig. 7 shows a beam scanning result diagram of the antenna device shown in Fig. 6; Figure 16

[0027] Fig. 8 shows another structure diagram of the antenna device provided by the embodiments of the present disclosure; Figure 18

[0028] Figure 19 Fig. 9 shows a beamforming result diagram using only a 2-Bit digital phase shifter;

[0029] Figure 20 Fig. 10 shows a beamforming result diagram using a 2-Bit digital phase shifter and an air interface phase shifter in combination;

[0030] Figure 21 Fig. 11 shows a flat-top beamforming theoretical calculation result diagram;

[0031] Figure 22 Fig. 12 shows a beam pointing diagram using only a 2-Bit digital phase shifter;

[0032] Figure 23 Fig. 13 shows a beam pointing diagram using a 2-Bit digital phase shifter and an air interface phase shifter in combination;

[0033] Figure 24 Fig. 14 shows a beam direction diagram using only a 2-Bit digital phase shifter;

[0034] Figure 25 Fig. 15 shows a beam direction diagram using a 2-Bit digital phase shifter and an air interface phase shifter in combination. DETAILED DESCRIPTION

[0035] In order to make the technical solutions of the present disclosure better understood, the embodiments of the present disclosure will be described in detail below with reference to the accompanying drawings.

[0036] The present disclosure will be described more fully hereinafter with reference to the accompanying drawings, in which embodiments of the present disclosure are shown. The present disclosure may, however, be embodied in many different forms and should not be construed as limited to the embodiments set forth herein. Rather, these embodiments are provided so that this disclosure will be thorough and complete, and will fully convey the scope of the present disclosure to those skilled in the art.

[0037] The accompanying drawings, which are included to provide a further understanding of the embodiments of the present disclosure and are incorporated in and constitute a part of this specification, illustrate embodiments of the present disclosure and together with the detailed description serve to explain the present disclosure. The above and other features and advantages of the present disclosure will become more apparent from the following detailed description, taken in conjunction with the accompanying drawings.

[0038] The present disclosure can be described with reference to plan views and / or cross-sectional views by virtue of the present disclosure ideal schematic views. Thus, the example schematic illustrations can not be necessarily drawn to scale and certain components can be exaggerated or omitted in order to better illustrate the present disclosure. ​

[0039] In the case of no conflict, the embodiments of the present disclosure and the features in the embodiments can be combined with each other.

[0040] The terms used in the present disclosure are only used to describe specific embodiments and are not intended to limit the present disclosure. The term "and / or" as used in the present disclosure includes any and all combinations of one or more of the associated listed items. The singular forms "a" and "the" as used in the present disclosure are also intended to include the plural forms, unless the context clearly indicates otherwise. The terms "comprising", "made of" as used in the present disclosure specify the presence of the features, integers, steps, operations, elements, and / or components, but do not exclude the presence or addition of one or more other features, integers, steps, operations, elements, components, and / or groups thereof.

[0041] Unless otherwise defined, all terms used in the present disclosure, including technical and scientific terms, have the same meaning as commonly understood by a person of ordinary skill in the art. It will also be understood that terms such as those defined in commonly used dictionaries should be interpreted as having a meaning that is consistent with their meaning in the context of the relevant art and the present disclosure, and should not be interpreted in an idealized or overly formal sense, unless expressly so defined in the present disclosure.

[0042] The present disclosure is not limited to the embodiments shown in the drawings, but includes modifications of the configuration formed based on the manufacturing process. Therefore, the regions exemplified in the drawings have a schematic property, and the shape of the regions shown in the drawings exemplifies the specific shape of the region of the element, but is not intended to be restrictive.

[0043] Existing phase shifters mainly include the following types: pull rod phase shifters, digital phase shifters, and spatial phase shifters, etc. Among them, the pull rod phase shifter adjusts the phase of the signal by changing the physical length of the transmission line. Such a phase shifter has the disadvantages of slow response speed, easy wear of mechanical parts, limited precision, etc., and cannot meet the demand for fast phase control in dynamic scenarios. The digital phase shifter is based on electronic switches, and adjusts the electrical characteristics of the antenna unit by changing the on or off state of the PIN diode, thereby realizing phase adjustment. The digital phase shifter often uses different bit positions (such as 2-Bit, 4-Bit, 8-Bit, etc.) to control the precision of phase adjustment. However, the digital phase shifter has the problems of large insertion loss and low phase control precision. The spatial phase shifter often realizes the control of electromagnetic wave phase in the form of transmission array or reflection array. The overall profile of the array of the spatial phase shifter is high, which is not conducive to equipment integration and limits the use scenarios. As can be seen from the above, the existing phase shifters have the problems of complex structure, large insertion loss, low precision, high overall profile of the array, etc.

[0044] To solve at least one of the above problems, please refer to Figure 1The embodiments of the present application provide a phase shift super surface structure 100, which is applied to an air interface phase shifter, for example, and is arranged on a dielectric plate (for example, a dielectric plate 1 shown in FIG. 1) of the air interface phase shifter. The phase shift super surface structure 100 includes at least two parallel resonators, and the lengths of at least some of the resonators are different. Figure 2 As shown in the three resonator structure, the at least two resonators include a first linear resonator 21 and two second linear resonators 22 arranged on both sides of the first linear resonator 21, for example. Figure 1

[0045] The stop band formed by the resonators refers to a region in which the propagation of electromagnetic waves is limited in a specific frequency band. The stop band is formed by introducing transmission zeros in the super surface. These transmission zeros can effectively prevent the propagation of electromagnetic waves in a specific frequency band. Based on this, the stop band formed by the resonators can achieve high-precision phase control in a specific frequency band. The length of the resonator is usually designed as an integer multiple of half a wavelength to achieve a specific phase response. By designing resonators of different lengths, different phase delays can be achieved, thereby providing more flexible phase control capabilities. Moreover, by using at least two parallel resonators, an array structure can be formed, so that the length and spacing of each resonator can be adjusted to comprehensively control the phase and amplitude of electromagnetic waves, thereby improving the performance of the phase shifter and achieving wider frequency coverage and more flexible phase control.

[0046] Specifically, the phase shift super surface is a two-dimensional metamaterial structure that can achieve phase control of electromagnetic waves on a subwavelength scale. By designing the geometry and size of the phase shift super surface structure 100, their response to electromagnetic waves can be determined to achieve a specific phase delay. Based on this principle, the phase shift super surface structure 100 provided by the present application can control the phase, amplitude and polarization of the incident electromagnetic wave to achieve phase delay of the incident electromagnetic wave and achieve high-precision phase control, which is suitable for application scenarios that require accurate beam control.

[0047] ​The stopband formed by the resonators refers to a region in which the propagation of electromagnetic waves is restricted within a specific frequency band. The formation of the stopband is achieved by introducing transmission zeros in the metasurface, which can effectively prevent the propagation of electromagnetic waves within a specific frequency band. Based on this, the stopband formed by the resonators can achieve high-precision phase control within a specific frequency band. The length of the resonator is usually designed as an integer multiple of half a wavelength to achieve a specific phase response. By designing resonators of different lengths, different phase delays can be achieved, thereby providing more flexible phase control capabilities. Moreover, by using at least two resonators parallel to each other, an array structure can be formed, thereby adjusting the length and spacing of each resonator to achieve comprehensive control of the phase and amplitude of electromagnetic waves, thereby improving the performance of the phase shifter and achieving a wider frequency coverage and more flexible phase control.

[0048] On this basis, at least one resonator is provided with at least one tuning device 4. By embedding the tuning device 4 in at least one resonator, dynamic control of the phase can be achieved. The tuning device 4, for example, includes at least one of a varactor, a PIN diode, a MEMS switch, and a ferroelectric material tuning unit, for adjusting the electrical size of the resonator in which it is located by changing its electrical parameters (such as capacitance, resistance, etc.), to achieve dynamic control of the phase. This dynamic adjustment capability makes the phase control continuous rather than fixed, allowing the phase shifter to respond in real time and achieve high-precision beam control and fast beam scanning, thereby improving the performance and flexibility of the phase shifter. Figure 8 The phase of the transmitted electromagnetic wave (in degrees) as a function of frequency is shown under different varactor capacitance conditions. Figure 8 The phase response curve in FIG. 4 shows the trend of phase change with frequency under different capacitance values. As can be seen, the phase change is related to the capacitance value, and by adjusting the capacitance value, the change in electromagnetic wave phase can be controlled, allowing precise control of the amplitude and phase of the transmitted electromagnetic wave. Taking the tuning device 4 as a varactor as an example, Figure 8 The relationship between the radiation phase (in degrees, ranging from -80 degrees to 40 degrees) and the capacitance value (in picofarads, ranging from 0.2 pF to 1.2 pF) is shown. Figure 8 The curve in FIG. 4 shows how the radiation phase changes as the capacitance value increases. Specifically, as the capacitance value increases, the radiation phase shows a downward trend. This indicates that the capacitance value is inversely proportional to the radiation phase, i.e., the larger the capacitance value, the lower the radiation phase. As can be seen, by changing the capacitance value of the varactor, the radiation phase can be controlled.

[0049] In some embodiments, as shown in FIG. 5, Figure 1As shown, in the phase-shifting metasurface structure 100, the at least two resonators include a first linear resonator 21 and at least two second linear resonators 22, wherein the first linear resonator 21 has the longest length, i.e., the length of the first linear resonator 21 is greater than the length of any second linear resonator 22. The at least two second linear resonators 22 are symmetrically distributed on both sides of the first linear resonator 21 along the width direction of the first linear resonator 21. By setting a longer resonator (the first linear resonator 21) and symmetrically setting shorter resonators (the second linear resonators 22) on both sides of the longer resonator, a specific array structure is formed. This structure can utilize resonators of different lengths to produce different phase responses at different frequencies, to achieve more complex phase control and thus improve the performance of the phase shifter.

[0050] Specifically, the first linear resonator 21 has the longest length, and the longer resonator can produce a larger phase delay at a lower frequency. The second linear resonators 22 are symmetrically distributed on both sides of the first linear resonator 21 to ensure that the electromagnetic wave maintains symmetry during propagation, thereby reducing inter-polarization crosstalk.

[0051] Further, in some embodiments, as shown in FIG. 2, there are multiple second linear resonators 22 on the same side, and the lengths of the second linear resonators 22 on the same side decrease in a direction away from the first linear resonator 21, which can achieve different phase responses. Figure 2

[0052] In other embodiments, as shown in FIG. 3, at least one second linear resonator 22 can be distributed on one side of the first linear resonator 21 along the width direction of the first linear resonator 21, and no second linear resonator 22 is arranged on the other side. This asymmetric structure can also utilize resonators of different lengths to produce different phase responses at different frequencies, to achieve more complex phase control and thus improve the performance of the phase shifter. Figure 3

[0053] It should be noted that in actual applications, as long as the phase-shifting metasurface structure 100 includes at least two resonators parallel to each other, and the lengths of at least some resonators are different, two transmission zeros of high and low can be formed by different electrical sizes, to achieve a frequency response of double stopbands. The tuner 4 (such as a varactor diode) is used to dynamically adjust the electrical size of the stopband, to achieve shifting of the transmission zero and thus phase adjustment.

[0054] In some examples, as shown in FIG. 4, the phase-shifting metasurface structure 100 includes a first linear resonator 21 and a second linear resonator 22, wherein the first linear resonator 21 has the longest length, and the second linear resonator 22 is arranged on one side of the first linear resonator 21 along the width direction of the first linear resonator 21. Figure 1 ​​As shown, the first linear vibrator 21 is one, and the second linear vibrator 22 is two. The first linear vibrator 21 is provided with a tuning device 4, which is arranged at the middle position of the first linear vibrator 21 in the length direction thereof, for example. Such a three-vibrator structure forms two transmission zeros by vibrators of different lengths, thereby realizing a frequency response of double stopband. Moreover, the three-vibrator structure has good symmetry, which can reduce cross-polarization compared with an asymmetric structure (such as a two-vibrator structure), and can improve polarization purity compared with a double circular ring or double square ring structure. By arranging the tuning device 4 on the central vibrator (i.e., the first linear vibrator 21) and adjusting the electrical parameters of the tuning device 4, the electrical size of the central vibrator (i.e., the first linear vibrator 21) is dynamically adjusted, thereby shifting the transmission zero and adjusting the phase. Moreover, the above three-vibrator structure only needs one tuning device 4 to tune the frequency response of one polarization, which is simple and has a low number of devices used.

[0055] In some embodiments, the three-vibrator structure is tuned by adjusting the electrical parameters of the tuning device 4. Figure 1 As an example of the above three-vibrator structure, the two ends of the first linear vibrator 21 are each provided with a circular arc-shaped portion 25, the middle position of the circular arc-shaped portion 25 is recessed (i.e., concave) relative to the two ends in a direction away from the end of the first linear vibrator 21, and is connected to the end of the first linear vibrator 21. By arranging the circular arc-shaped portion 25 at the two ends of the first linear vibrator 21, the electrical size of the vibrator can be optimized, and by recessing the middle position of the circular arc-shaped portion 25 relative to the two ends in a direction away from the end of the first linear vibrator 21, the reflection and scattering of electromagnetic waves at the end of the vibrator can be reduced, thereby reducing the required physical length and achieving miniaturization. The circular arc-shaped portion 25 can optimize the propagation path of electromagnetic waves, reduce transmission loss, and improve the transmission efficiency of electromagnetic waves, thereby reducing the required physical length and achieving miniaturization. The circular arc-shaped portion 25 is connected to the end of the first linear vibrator 21 to form a continuous structure, and the connection mode is, for example, integrated.

[0056] In some embodiments, the three-vibrator structure is tuned by adjusting the electrical parameters of the tuning device 4. Figure 1As shown in the three-vibrator structure, the two ends of the first linear vibrator 21 are respectively connected with an input terminal 26 and an output terminal 27, the input terminal 26 is used for inputting a direct current signal, and the output terminal 27 is used for grounding; the input terminal 26 and the output terminal 27 are both provided with an inductor 5. Specifically, the input terminal 26 is used for inputting a direct current signal to provide a bias voltage for a resonant device (for example, a varactor). The direct current signal enters the first linear vibrator 21 through the input terminal 26 to provide a necessary electric field for the varactor, so as to realize dynamic adjustment of the electric size of the first linear vibrator 21. The output terminal 27 is used for grounding to ensure stable return flow of the direct current signal, effectively reduce electromagnetic interference, and improve the stability of the system. The input terminal 26 and the output terminal 27 are both provided with an inductor 5, the inductor 5 shows low impedance to the direct current signal, which facilitates the provision of a stable bias voltage for the resonant device, and shows high impedance to the radio frequency signal to effectively prevent radio frequency energy from leaking to the direct current path, thereby playing a role of isolating the direct current signal and the radio frequency signal in the circuit, and further reducing electromagnetic interference and improving the stability of the system.

[0057] As can be seen from the above, by designing vibrators with different lengths, high-precision phase control can be realized, which is suitable for application scenarios requiring precise beam control, and a wider frequency coverage can be realized to meet various application requirements. Preferably, through the symmetrical layout of multiple vibrators, high-purity dual-polarization characteristics can be realized to ensure independent control of two orthogonal polarized signals. In actual applications, the symmetrical layout of multiple vibrators is not limited to the three-vibrator structure, and other numbers of second linear vibrators 22 can also be used, and the tuning device 4 can also be arranged on the second linear vibrator 22, for example, as shown in the following example. Figure 4 As shown in the example, the first linear vibrator 21 is one, the second linear vibrator 22 is four, and is symmetrically distributed on both sides of the first linear vibrator 21 along the width direction of the first linear vibrator 21; each second linear vibrator 22 adjacent to the first linear vibrator 21 is provided with a tuning device 4. The tuning device 4 is arranged at the middle position of the second linear vibrator 22 in the length direction of the second linear vibrator 22, for example.

[0058] In the above example, the phase-shifting metasurface structure 100 includes linear vibrators, but the embodiments of the present application are not limited thereto, and in other examples, as shown in the following example. Figure 5As shown, the phase-shifting metasurface structure 100 can include linear oscillators 23 and non-linear oscillators 24 distributed around (i.e., encircling) the linear oscillators 23, or distributed on both sides of the linear oscillators 23 in the width direction of the linear oscillators 23. The length of the linear oscillators 23 is different from the length of the non-linear oscillators 24; the linear oscillators 23 are provided with a tuning device 4. The tuning device 4 is provided, for example, at the middle position of the linear oscillators 23 in the length direction thereof. Specifically, the non-linear oscillators 24 can adopt a curved, ring-shaped or other complex-shaped structure. By combining the linear oscillators 23 and the non-linear oscillators 24, more complex phase control can be achieved, thereby improving the performance of the phase shifter and achieving a wider frequency coverage. On this basis, by using linear oscillators 23 and non-linear oscillators 24 of different lengths, different phase delays can be achieved, and the oscillators of different lengths will produce different phase responses in a specific frequency range to achieve more accurate phase control, thereby improving the performance of the phase shifter. In addition, the oscillators of different lengths can reduce crosstalk at different frequencies, thereby improving the stability and reliability of the system.

[0059] The combination of the linear oscillators 23 and the non-linear oscillators 24 can form various structures, for example, as shown in Figure 5 As shown, the non-linear oscillators 24 are a closed body connected at the head and tail and distributed around the linear oscillators 23. The closed body is, for example, a circular ring. For another example, as shown in Figure 6 As shown, the non-linear oscillators 24 include at least two circular-arc-shaped oscillators and are symmetrically distributed on both sides of the linear oscillators 23 in the width direction thereof. For another example, as shown in Figure 7 As shown, the non-linear oscillators 24 include at least two circular-arc-shaped oscillators with a bending portion 241, and are symmetrically distributed on both sides of the linear oscillators 23 in the width direction thereof, the bending portion 241 being recessed in a direction away from the center of the circular-arc-shaped oscillators.

[0060] As another technical solution, please refer to Figure 9 and Figure 10 The embodiments of the present application also provide a phase-shifting metasurface structure 100', which is different from the above-mentioned embodiments in that it includes a first closed body 02 connected at the head and tail and a second closed body 03 connected at the head and tail. The first closed body 02 and the second closed body 03 can be arranged in the same layer or different layers. Taking the case of applying the phase-shifting metasurface structure 100' to an air interface phase shifter, the first closed body 02 and the second closed body 03 can be arranged on two surfaces of a dielectric plate 1 of the air interface phase shifter, i.e., arranged in different layers; or, they can also be arranged on the same surface of the two surfaces of the dielectric plate 1 of the air interface phase shifter, i.e., arranged in the same layer. For example, Figure 9 The first closed body 02 and the second closed body 03 in are arranged on the two surfaces of the dielectric plate 1, respectively, wherein the second closed body 03 is locatedFigure 9 The back side of medium plate 1 is shown in dashed lines.

[0061] Furthermore, the first closed body 02 and the second closed body 03 have the same shape but different dimensions. The stopband formed by the closed bodies can also achieve high-precision phase control within a specific frequency band. By designing closed bodies of different dimensions (e.g., circumferential length), different phase delays can be achieved, thereby providing more flexible phase control capabilities.

[0062] In some embodiments, the first closed body 02 and the second closed body 03 are nested together and extend parallel to each other in the circumferential direction. By employing the first closed body 02 and the second closed body 03 extending parallel to each other in the circumferential direction, an array structure can be formed. This allows for comprehensive control of the phase and amplitude of electromagnetic waves by adjusting the circumferential length of each closed body and the spacing between the first closed body 02 and the second closed body 03, thereby improving the performance of the phase shifter and achieving wider frequency coverage and more flexible phase control.

[0063] Based on this, at least one of the first closed body 02 and the second closed body 03 is provided with at least one tuning device 4 for realizing continuous phase modulation of the polarization signal. In some embodiments, there are multiple tuning devices 4 provided on the first closed body 02 and they are uniformly distributed in the circumferential direction of the first closed body 02; and / or, there are multiple tuning devices 4 provided on the second closed body 03 and they are uniformly distributed in the circumferential direction of the second closed body 03.

[0064] In a specific embodiment, such as Figure 9 As shown, both the first closed body 02 and the second closed body 03 are circular rings, arranged in opposite layers, for example, located on opposite surfaces of the dielectric plate 1 of the air-port phase shifter. The smaller ring has four tuning devices 4, which are evenly distributed around its circumference, while the larger ring has no tuning devices 4. The tuning devices 4 are, for example, varactor diodes. By adjusting the capacitance of the varactor diodes, the electrical dimensions of the smaller ring can be changed. Thus, the two rings can achieve continuous phase modulation of two orthogonally polarized electromagnetic waves.

[0065] In another specific embodiment, such as Figure 10 As shown, both the first closed body 02 and the second closed body 03 are square rings, and the two square rings are arranged in the same layer. For example, they are located on the same surface of two opposing surfaces of the dielectric plate 1 of the air port phase shifter. For example, both square rings are located on... Figure 10Front side of the dielectric plate 1. The small-sized square ring is provided with four tuning devices 4, which are evenly distributed in the circumferential direction of the small-sized square ring, while the large-sized square ring is not provided with tuning devices 4. Among them, the tuning device 4 is, for example, a varactor, by adjusting the capacitance of the varactor, the electrical size of the small-sized square ring can be changed, thereby the two square rings can realize the continuous phase control of two orthogonal linearly polarized electromagnetic waves.

[0066] The other structures and functions of the phase-shifting metasurface structure 100' provided by the embodiments of the present application are the same as or similar to those of the phase-shifting metasurface structure 100 provided by the above-mentioned embodiments, and will not be described here again.

[0067] As another technical solution, the embodiments of the present application also provide an air interface phase shifter, which can realize independent and continuous phase control of two orthogonal linearly polarized electromagnetic waves, and by using the metasurface air interface phase control technology, the phase-shifting function can be directly integrated with the radiating antenna, not only reducing the signal transmission path and reducing the insertion loss, but also improving the system integration. In addition, by using the tuning device 4 for dynamic tuning, the number of tuning devices 4 can be reduced, and the high loss and volume problems caused by the cascaded circuit of the traditional phase shifter can be avoided.

[0068] Specifically, please refer to Figure 11 The air interface phase shifter 1000 provided by the embodiments of the present application includes at least one dielectric plate 1 and a first phase-shifting metasurface structure 2 and a second phase-shifting metasurface structure 3 arranged on each dielectric plate 1, wherein the dielectric plate 1 is the physical support structure of the phase shifter, which is usually made of low-loss dielectric materials such as polytetrafluoroethylene (PTFE) or ceramic. The dielectric plate 1 serves to support the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3, and provides a stable platform to realize the propagation and control of electromagnetic waves.

[0069] The first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 both adopt the phase-shifting metasurface structure 100 provided by the above-mentioned embodiments of the present application or adopt the phase-shifting metasurface structure 100' provided by the above-mentioned embodiments of the present application.

[0070] In some embodiments, as Figure 11 and Figure 12As shown, the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 are respectively arranged on the two surfaces of the dielectric plate 1 facing away from each other, and are arranged orthogonally, for independently phase-controlling two orthogonal polarized signals. Specifically, the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 can both control the phase, amplitude and polarization of the incident electromagnetic wave, to realize phase delay of the incident electromagnetic wave, realize high-precision phase control, and be suitable for application scenarios requiring accurate beam control. Moreover, by designing different phase-shifting metasurface structures, different phase responses can be realized to meet different application requirements. On this basis, by arranging the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 on the two surfaces of the dielectric plate 1 facing away from each other, independent control of the two orthogonal polarized signals can be realized, and the two polarized signals are physically separated and do not interfere with each other. By arranging the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 orthogonally, high-purity dual-polarization characteristics can be realized.

[0071] Specifically, the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 can realize different phase delays by designing different lengths of the resonators, thereby providing more flexible phase control capabilities, by using the phase-shifting metasurface structure 100 provided in each of the above embodiments of the present application. Moreover, by using at least two resonators parallel to each other, an array structure can be formed, so that the length and spacing of each resonator can be adjusted to realize comprehensive control of the phase and amplitude of the electromagnetic wave, thereby improving the performance of the phase shifter and realizing wider frequency coverage and more flexible phase control.

[0072] In some embodiments, as shown in FIG. 1, Figure 12 As shown, the orthographic projection of the first phase-shifting metasurface structure 2 on the dielectric plate 1 coincides with the orthographic projection of the second phase-shifting metasurface structure 3 on the dielectric plate 1 after being rotated by 90°, i.e., the shape and size of the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 are the same, and the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 are geometrically orthogonal. For example, Figure 12 The orthographic projection of the first phase-shifting metasurface structure 2 in FIG. 1 on the dielectric plate 1 can coincide with the orthographic projection of the second phase-shifting metasurface structure 3 on the dielectric plate 1 after being rotated by 90° counterclockwise. The above phase-shifting metasurface structure is relatively simple, has low complexity, and is easy to design and implement.

[0073] On this basis, by embedding the tuning device 4 in at least one resonator, dynamic control of the phase can be realized. This dynamic adjustment capability makes the phase control continuous rather than fixed, so that the phase shifter can respond in real time, realize high-precision beam control and fast beam scanning, and improve the performance and flexibility of the phase shifter.

[0074] In some examples, as shown in FIG. 1,Figure 11 As shown, at least one oscillator in both the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 is equipped with at least one tuning device 4. In this case, the tuning devices 4 of the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 are used to independently perform phase modulation on two orthogonal polarization signals, improving the system's flexibility and performance. For example, in a dual-polarization communication system, the beam directions of the horizontally polarized and vertically polarized signals can be controlled independently, thereby achieving higher spectral efficiency and better communication quality.

[0075] In other examples, at least one oscillator in the first phase-shifting metasurface structure 2 may be provided with at least one tuning device 4, while the second phase-shifting metasurface structure 3 may not be provided with tuning device 4; or at least one oscillator in the second phase-shifting metasurface structure 3 may be provided with at least one tuning device 4, while the first phase-shifting metasurface structure 2 may not be provided with tuning device 4.

[0076] This embodiment utilizes a first phase-shifting metasurface structure 2 and a second phase-shifting metasurface structure 3, along with a tuning device 4, to adjust the electrical dimensions of the oscillator. This enables independent and continuous phase control of two orthogonally linearly polarized electromagnetic waves, significantly improving system flexibility and accuracy while avoiding the complexity of using two independent phase shifters. Furthermore, by employing metasurface open-aperture phase control technology, the phase-shifting function can be directly integrated with the radiating antenna, reducing signal transmission paths and insertion loss. It also improves system integration, making it particularly suitable for high-density array integration, reducing system size and increasing system reliability. Moreover, dynamic tuning via the tuning device 4 reduces the number of tuning devices, avoiding the high losses and size issues associated with cascaded circuits in traditional phase shifters.

[0077] There can be one or more dielectric substrates 1. In the case of multiple dielectric substrates 1, such as... Figure 13 As shown, multiple dielectric plates 1 are arranged opposite each other and spaced apart along a direction perpendicular to the dielectric plates 1, forming a multi-layer structure to increase the total phase shift and thus achieve a larger phase control range. The more dielectric plates 1 there are, the greater the total phase shift. In practical applications, different numbers of dielectric plates 1 can be selected according to actual application requirements to achieve different phase shifts and improve system flexibility. Multiple dielectric plates 1 arranged opposite each other along a direction perpendicular to the dielectric plates 1 means that the orthographic projections of the multiple dielectric plates 1 onto any one of the dielectric plates 1 at least partially overlap.

[0078] The number of the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 of each dielectric plate 1 can be one or multiple. The multiple first phase-shifting metasurface structures 2 and the multiple second phase-shifting metasurface structures 3 of each dielectric plate 1 are arranged one by one. That is, the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 are arranged in pairs, and multiple pairs of the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 share the same dielectric plate 1, so that the integration of the phase shifter can be improved. The multiple first phase-shifting metasurface structures 2 and the multiple second phase-shifting metasurface structures 3 can be periodically arranged, for example, the multiple first phase-shifting metasurface structures 2 are arranged in a row, and correspondingly, the multiple second phase-shifting metasurface structures 3 are arranged in a row. Of course, in actual application, the multiple first phase-shifting metasurface structures 2 can also be arranged in an array.

[0079] As another technical solution, please refer to Figure 14 to Figure 16 The embodiment of the present application also provides an antenna device 2000 which can be applied to various communication environments requiring accurate beam control and dynamic adjustment, especially to 5G communication, radar system, etc.

[0080] The antenna device 2000 includes the above-mentioned air interface phase shifter 1000 provided by the embodiment of the present application, and a radiating antenna 200 which is cascaded with the air interface phase shifter 1000. Specifically, the air interface phase shifter 1000 includes at least one dielectric plate 1, and at least one pair of first phase-shifting metasurface structure 2 and second phase-shifting metasurface structure 3 is arranged on each dielectric plate 1, which are respectively used for independently phase regulating two orthogonal polarized signals. Moreover, by embedding a tuning device 4 (such as a varactor) in at least one of the oscillators of the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3, the electrical size of the oscillator can be dynamically adjusted, so as to realize accurate regulation of the electromagnetic wave phase, and then the phase shifter can realize real-time response, and realize high-precision beam control and fast beam scanning.

[0081] The radiating antenna 200 is used for transmitting and receiving electromagnetic waves. In some embodiments, the radiating antenna 200, for example, includes a dual-polarized patch antenna, which is a kind of antenna unit capable of supporting two orthogonal polarization directions (such as horizontal polarization and vertical polarization) at the same time, and can be a dual-polarized probe-fed radiating patch antenna. Such an antenna unit can process two independent signals at the same time, improving the capacity and flexibility of the communication system. The number of dual-polarized patch antennas is the same as the number of first phase-shifting metasurface structures 2 provided on each dielectric plate 1, and each dual-polarized patch antenna is arranged opposite to each phase-shifting metasurface structure (at least one of the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3) provided on the adjacent dielectric plate 1 in a direction perpendicular to the dielectric plate 1. By arranging the dual-polarized patch antenna opposite to the corresponding first phase-shifting metasurface structure 2 provided on the adjacent dielectric plate 1, the phase of the electromagnetic wave is accurately regulated when passing through the corresponding first phase-shifting metasurface structure 2 and second phase-shifting metasurface structure 3, thereby realizing dynamic shaping and flexible pointing of the beam. It should be noted that the electrical parameters (such as capacitance, resistance, etc.) of the tuning devices 4 of the plurality of first phase-shifting metasurface structures 2 on the same dielectric plate 1 are the same; the electrical parameters (such as capacitance, resistance, etc.) of the tuning devices 4 of the plurality of second phase-shifting metasurface structures 3 on the same dielectric plate 1 are the same.

[0082] As shown in Figure 16 , by adjusting the electrical parameters of the tuning devices 4 of the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3 respectively, the first polarized beam and the second polarized beam can be independently regulated respectively, realizing independent deflection of the two. Figure 17 The beam scanning results of the antenna device 2000 shown in Figure 16 include the gain patterns of two different polarization directions. Figure 17 Curves 1 and 2 in Figure 17 show the gain (in dBi, ranging from -30dBi to 0dBi) at different angles (Theta, in degrees, ranging from -90 degrees to 90 degrees). As can be seen from Figure 17 , the shapes and directions of curves 1 and 2 are similar, and by adjusting the electrical parameters of the tuning devices 4 of the first phase-shifting metasurface structure 2 and the second phase-shifting metasurface structure 3, the first polarized beam and the second polarized beam can be independently regulated, realizing independent deflection of the beams. However, there is a phase difference between curves 1 and 2, indicating that the two polarized beams can be independently regulated and do not interfere with each other, which can indicate that the polarization purity of the dual-polarized air interface phase shifter is good, i.e., the beams in each polarization direction are relatively independent in space.

[0083] In some embodiments, as shown in Figure 18As shown, the antenna device 2000 further includes digital phase shifters 300, the number of which is the same as that of the radiating antennas 200 (i.e., dual-polarized patch antennas), and each of which is arranged on the side of each radiating antenna 200 (i.e., dual-polarized patch antenna) away from the air interface phase shifter 1000 in a one-to-one correspondence. Specifically, the digital phase shifter 300 is an electronic switch-based phase shifter that adjusts the electrical characteristics of the antenna unit by changing the on or off state of the PIN diode to achieve phase adjustment. The digital phase shifter 300 usually uses different bit positions (such as 2-Bit, 4-Bit, 8-Bit, etc.) to control the accuracy of phase adjustment. With the increase of bit positions, the phase adjustment steps are more detailed, thereby improving the accuracy of phase control. By arranging each digital phase shifter 300 in a one-to-one correspondence with a radiating antenna 200 (i.e., dual-polarized patch antenna), it can be ensured that the phase of each radiating antenna 200 (i.e., dual-polarized patch antenna) can be independently regulated, thereby improving the flexibility and performance of the system.

[0084] Moreover, the digital phase shifter 300 achieves high-precision phase adjustment through different bit positions, which is suitable for application scenarios that require precise beam control. In a specific embodiment, each digital phase shifter 300 uses a 2-Bit design, providing four discrete phases (0°, 90°, 180°, 270°). By using the digital phase shifter 300, the radiating antenna 200 (i.e., dual-polarized patch antenna), and the air interface phase shifter 1000 in combination, 360° continuous phase modulation is achieved. On this basis, by regulating the electrical parameters (such as capacitance, resistance, etc.) of the tuning devices 4 in the air interface phase shifter 1000, precise regulation of the array radiated electromagnetic beam can be achieved. The combination of the digital phase shifter 300, the radiating antenna 200 (i.e., dual-polarized patch antenna), and the air interface phase shifter 1000 can achieve various functions, such as 60° flat beamforming, 45° precise beam pointing, and the formation of low-sidelobe, high-gain beams. This combination has significant advantages in modern communication and radar systems and is suitable for application scenarios that require high precision and fast beam scanning. In a specific embodiment, as shown, Figure 18 As shown, the air interface phase shifter 1000 includes three dielectric plates 1, each of which is provided with a row of first phase-shifting metasurface structures 2 and a row of second phase-shifting metasurface structures 3, each row of first phase-shifting metasurface structures 2 and each row of second phase-shifting metasurface structures 3 have 8, and are in one-to-one correspondence. On this basis, by regulating the electrical parameters (such as capacitance, resistance, etc.) of the tuning devices 4 in the air interface phase shifter 1000, precise regulation of the array radiated electromagnetic beam can be achieved, achieving 90° continuous phase adjustment, and on this basis, in combination with the 2-Bit digital phase shifter 300, 360° continuous phase adjustment can be achieved.

[0085] The antenna device 2000 described above can perform 60° flat-top beamforming. Specifically, the antenna device 2000 shown in FIG. 2B can perform 60° flat-top beamforming by combining the discrete phase control of the 2-Bit digital phase shifter with the 90° continuous phase adjustment of the air interface phase shifter 1000. Figure 18 For example, the antenna device 2000 shown in FIG. 2B can achieve arbitrary phase control by combining the discrete phase control of the 2-Bit digital phase shifter with the 90° continuous phase adjustment of the air interface phase shifter 1000. According to the design target, an optimization algorithm can be used to calculate the feed phase weight value to achieve 60° flat-top beamforming, and to determine the radiation phase of each dual-polarized patch antenna. The specific amplitude, accurate phase weight value, and 2-Bit discrete phase weight value are shown in Table 1 below.

[0086] Table 1

[0087]

[0088] Figure 19 and Figure 20 respectively show the beamforming results using only the 2-Bit digital phase shifter and combining the 2-Bit digital phase shifter and the air interface phase shifter 1000 (discrete + continuous), specifically showing the gain (in dBi) of the antenna device at different angles. Comparing Figure 19 and Figure 20 it can be seen that Figure 19 the 2-Bit digital phase shifter in provides four discrete phases (0°, 90°, 180°, 270°), and due to the discreteness of phase adjustment, the flat-top beam in the beamforming result has a large depression. This means that in some angle range, the gain decreases significantly, and the ideal flat-top beam shape cannot be achieved. This beam shape is quite different from the flat-top beamforming theoretical calculation result shown in Figure 21 , and precise beam control cannot be achieved. As Figure 20 can be seen, by combining the 2-Bit digital phase shifter and the air interface phase shifter 1000, the discrete and continuous phase adjustment capabilities are utilized, and more smooth and accurate beamforming can be achieved, and the shape of the flat-top beam is closer to the flat-top beamforming theoretical calculation result shown in Figure 21 . This beam shape can better cover the desired direction, improve the quality and coverage range of the signal, and is suitable for the demand for precise beam control in high-performance communication systems.

[0089] The antenna device 2000 described above can also perform 45° precise beam pointing, specifically, the antenna device 2000 shown in FIG. 2B can perform 45° precise beam pointing by combining the discrete phase control of the 2-Bit digital phase shifter with the 90° continuous phase adjustment of the air interface phase shifter 1000. Figure 18The antenna device 2000 shown is an example, through the discrete phase control of the 2-Bit digital phase shifter combined with the 90° continuous phase adjustment of the air interface phase shifter 1000, arbitrary phase control can be realized. According to the design target, the feeding phase weight value for realizing 60° flat beam shaping can be calculated using an optimization algorithm to determine the radiation phase (relative) of each dual-polarized patch antenna. The specific accurate phase weight value and 2-Bit discrete phase weight value are shown in Table 2 below.

[0090] Table 2

[0091]

[0092] Figure 22 and Figure 23 respectively show the beam pointing using only a 2-Bit digital phase shifter and combining a 2-Bit digital phase shifter and an air interface phase shifter 1000 (discrete + continuous), specifically showing the gain (in dBi) of the antenna device at different angles. Comparing Figure 22 and Figure 23 we can see that Figure 22 only using a 2-Bit digital phase shifter provides limited discrete phase control (e.g. 0°, 90°, 180°, 270°), which limits its ability to fine-tune the beam. From Figure 22 we can see that although the 2-Bit digital phase shifter can achieve basic beam shaping, it performs poorly in terms of beam pointing accuracy and sidelobe suppression. Especially in application scenarios that require high-precision beam control, the 47° pointing deviation of the beam and the high sidelobe level can negatively affect the performance of the communication system, such as reducing signal clarity and increasing interference. This beam shape can lead to uneven coverage, affecting signal quality, especially in applications where beam pointing accuracy is required. From Figure 23 we can see that by combining the use of a 2-Bit digital phase shifter and an air interface phase shifter 1000, the discrete and continuous phase adjustment capabilities are utilized, resulting in a more smooth beam shape, higher gain in the main beam direction, and lower sidelobe, showing better beam shaping ability. This beam shape can more accurately cover the desired direction, improving signal quality and coverage.

[0093] The above antenna device 2000 can also achieve low sidelobe beam, high gain, specifically, with Figure 18The antenna device 2000 shown is an example. By combining the discrete phase control of the 2-Bit digital phase shifter with the 90° continuous phase adjustment of the air interface phase shifter 1000, arbitrary phase control can be achieved. According to the design target, an optimization algorithm can be used to calculate the feed phase weight value to achieve low sidelobe and high gain beam, and to determine the radiation phase (relative) of each dual-polarized patch antenna. The specific accurate phase weight value and the 2-Bit discrete phase weight value are shown in Table 3 below.

[0094] Table 3

[0095]

[0096] Figure 24 and Figure 25 respectively show the beam direction using only a 2-Bit digital phase shifter and a combination of a 2-Bit digital phase shifter and an air interface phase shifter 1000 (discrete + continuous), specifically showing the gain of the antenna device at different angles (in dBi). Comparing Figure 23 and Figure 24 we can see that Figure 23 only using a 2-Bit digital phase shifter provides limited discrete phase control (e.g. 0°, 90°, 180°, 270°), which limits its ability to fine-tune the beam. From Figure 24 we can see that the maximum gain is about 14.5dBi, showing limited gain capability. In addition, the highest sidelobe reaches 6.5dBi, indicating a deficiency in sidelobe suppression. This beam shape may not meet the system performance requirements in application scenarios with strict requirements for low sidelobe and high gain, which may lead to increased signal interference and reduced coverage. From Figure 25 we can see that by combining the use of a 2-Bit digital phase shifter and an air interface phase shifter 1000, the discrete and continuous phase adjustment capabilities are utilized to fine-tune the phase. Figure 25 The maximum gain reaches 15.3dBi in the above, which is significantly improved compared to the scheme of using only a 2-Bit digital phase shifter. At the same time, the highest sidelobe is effectively suppressed to 2dBi, significantly improving the beam shape and energy distribution. This beam shape shows better main lobe energy concentration and lower sidelobe energy leakage, thereby improving system gain and reducing interference, suitable for high-performance communication systems with high requirements for beam control accuracy.

[0097] In summary, the antenna device 2000 provided by the embodiment of the present application realizes comprehensive optimization of beamforming, accurate pointing, high gain, and low sidelobe and other performances by combining the use of a 2-Bit digital phase shifter and an air interface phase shifter 1000. Specifically, the 2-Bit digital phase shifter provides fast phase adjustment capability and can quickly respond to the instantaneous demand of the system for beam direction. The air interface phase shifter 1000 allows fine control of the phase to achieve higher precision beam control. Moreover, the shape of the beam can be flexibly controlled to adapt to different coverage requirements. In addition, the antenna device provided by the embodiment of the present application can realize accurate pointing of the beam, optimize the directivity of the signal, and improve the communication quality; the optimized beam shape helps to improve the gain of the antenna array, thereby enhancing the transmission distance and strength of the signal. In addition, by suppressing the sidelobe, unnecessary energy leakage is reduced, the clarity of the signal is improved, and the interference on other users is reduced.

[0098] The present disclosure has disclosed example embodiments, and although specific terms are employed, they are used in the broadest descriptive sense only and should not be construed to limit the disclosure. In some instances, it will be apparent to those skilled in the art that features, characteristics, and / or elements described in connection with a particular embodiment can be used in conjunction with other embodiments unless otherwise explicitly stated. Thus, those skilled in the art will understand that various changes in form and detail can be made without departing from the scope of the disclosure as set forth in the appended claims.

Claims

1. An air-to-ground phase shifter, characterized in that, It includes at least one dielectric substrate and a first phase-shifting metasurface structure and a second phase-shifting metasurface structure disposed on each of the dielectric substrates, wherein the first phase-shifting metasurface structure and the second phase-shifting metasurface structure both adopt the same phase-shifting metasurface structure; The phase-shifting metasurface structure includes at least two parallel oscillators, and at least some of the oscillators have different lengths; at least one of the oscillators is provided with at least one tuning device, which is used to adjust the electrical dimensions of the oscillator by changing its own electrical parameters, so that the phase modulation is continuous; The at least two oscillators include a first linear oscillator and at least two second linear oscillators; the at least two second linear oscillators are symmetrically distributed on both sides of the first linear oscillator along its width direction; The first phase-shifting metasurface structure and the second phase-shifting metasurface structure are disposed on the same surface or different surfaces of two opposing surfaces of the dielectric plate, and the first phase-shifting metasurface structure and the second phase-shifting metasurface structure are orthogonally arranged.

2. The air-port phase shifter according to claim 1, characterized in that, The first linear oscillator has the longest length.

3. The air-port phase shifter according to claim 2, characterized in that, There is one first linear vibrator and two second linear vibrators, with the first linear vibrator equipped with the tuning device; or... There is one first linear vibrator and four second linear vibrators. Each of the second linear vibrators adjacent to the first linear vibrator is equipped with the tuning device.

4. The air-port phase shifter according to claim 2, characterized in that, The tuning device is positioned at the midpoint of the first linear oscillator along its length.

5. The air-port phase shifter according to claim 2, characterized in that, Both ends of the first linear vibrator are provided with arc-shaped portions, the middle position of which is recessed relative to the two ends toward the ends away from the first linear vibrator and is connected to the ends of the first linear vibrator.

6. The air-port phase shifter according to claim 2, characterized in that, The first linear vibrator has an input terminal and an output terminal connected to its two ends, respectively. The input terminal is used to input DC signals, and the output terminal is used to ground. Both the input terminal and the output terminal are equipped with inductors.

7. The air-port phase shifter according to claim 1, characterized in that, The first phase-shifting metasurface structure and the second phase-shifting metasurface structure are respectively disposed on two opposing surfaces of the dielectric plate; after rotating 90°, the orthographic projection of the first phase-shifting metasurface structure on the dielectric plate coincides with the orthographic projection of the second phase-shifting metasurface structure on the dielectric plate.

8. An antenna device, characterized in that, include: The air interface phase shifter as described in any one of claims 1 to 7; A radiating antenna is cascaded with the air interface phase shifter.

9. The antenna device according to claim 8, characterized in that, The radiating antenna includes a dual-polarized patch antenna, the number of which is the same as the number of the first phase-shifting metasurface structures disposed on each of the dielectric substrates, and each of the dual-polarized patch antennas is disposed in a one-to-one correspondence with one of the first phase-shifting metasurface structures and one of the second phase-shifting metasurface structures disposed on the adjacent dielectric substrates, arranged in a direction perpendicular to the dielectric substrate.

10. The antenna device according to claim 9, characterized in that, It also includes a digital phase shifter, which is configured in a one-to-one correspondence with the dual-polarized patch antenna, and the digital phase shifter is positioned relative to the side of the corresponding dual-polarized patch antenna away from the air interface phase shifter.

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