Phase shifter and antenna

Abstract

The invention discloses a phase shifter and an antenna. The phase shifter comprises at least one phase shifting unit, the phase shifting unit comprises a phase shifter wire, an adjustable dielectric layer and a grounding electrode layer, the phase shifter wire comprises a main wire and at least one branch wire in cross connection with the main wire, and the grounding electrode layer comprises at least one patterned area. The patterned region comprises at least two sub-hollow-out regions arranged along the first direction and a part of the grounding electrode layer between the adjacent sub-hollow-out regions. The orthographic projection of the branch wiring on the plane where the grounding electrode layer is located is located between the orthographic projections of the two adjacent sub-hollowed-out areas on the plane where the grounding electrode layer is located and is overlapped with the grounding electrode layer between the two adjacent sub-hollowed-out areas. According to the phase shifter and the antenna provided by the embodiment of the invention, larger phase change can be realized in a shorter physical length, so that the length of the routing of the phase shifter can be shortened, the loss of a radio frequency signal on the routing of the phase shifter is reduced, and the beam quality and the radiation power are improved.

Description

Technical Field

[0001] This invention relates to the field of communication technology, and in particular to a phase shifter and antenna. Background Technology

[0002] Liquid crystal antennas are novel array antenna structures that combine traditional microstrip patch antennas with liquid crystal materials. As the most crucial component of a liquid crystal antenna array, the performance of the liquid crystal phase shifter directly impacts the overall performance of the array. The principle of a liquid crystal phase shifter is to use liquid crystal material as the dielectric substrate of a traditional microstrip line. By changing the bias voltage applied to the microstrip line, the deflection characteristics of the liquid crystal molecules are controlled, thereby altering the effective dielectric constant of the liquid crystal and adjusting the phase of the electromagnetic wave.

[0003] To meet the growing trend of miniaturization and thinning of modern electronic devices, the cell thickness of liquid crystal phase shifters is typically designed to be very small. However, under low cell thickness conditions, existing liquid crystal phase shifters suffer from significant signal loss, affecting the beam quality and radiated power of the antenna. Summary of the Invention

[0004] This invention provides a phase shifter and an antenna to improve the beam quality and radiated power of the antenna.

[0005] According to one aspect of the present invention, a phase shifter is provided, comprising at least one phase shifting unit, the phase shifting unit comprising a phase shifter trace, an adjustable dielectric layer and a ground electrode layer, the phase shifter trace and the ground electrode layer being disposed opposite to each other, and the adjustable dielectric layer being located between the phase shifter trace and the ground electrode layer;

[0006] The phase shifter trace includes a main trace and at least one branch trace that intersects and connects with the main trace. The ground electrode layer includes at least one patterned region. The patterned region includes at least two sub-cutout regions arranged along a first direction and a portion of the ground electrode layer between adjacent sub-cutout regions. The first direction is parallel to the extension direction of the main trace.

[0007] The orthographic projection of the branch trace on the plane where the ground electrode layer is located lies between the orthographic projections of the two adjacent sub-cutout regions on the plane where the ground electrode layer is located, and overlaps with the ground electrode layer between the two adjacent sub-cutout regions.

[0008] According to another aspect of the present invention, an antenna is provided, characterized in that it includes the phase shifter described in the first aspect.

[0009] The phase shifter and antenna provided in the embodiments of the present invention include a main trace and at least one branch trace that intersects and connects with the main trace. The ground electrode layer includes at least one patterned region. The patterned region includes at least two sub-cutout regions arranged along a first direction and a portion of the ground electrode layer between adjacent sub-cutout regions. The first direction is parallel to the extension direction of the main trace. The sub-cutout region 301 and the overlapping main trace portion constitute a defective ground structure, introducing equivalent inductance into the phase shifter trace. The orthogonal projection of the stub trace onto the plane of the ground electrode layer is located between two adjacent sub-cutout regions and overlaps with the ground electrode layer between two adjacent sub-cutout regions, forming an open-circuit short stub structure, thereby introducing equivalent capacitance into the phase shifter trace. This increases the distributed inductance and distributed capacitance on the phase shifter trace, reduces the phase velocity and wavelength, and achieves a slow wave effect. As a result, the same or greater phase change can be achieved within a shorter physical length, which can significantly shorten the length of the phase shifter trace, reduce the transmission path length of the RF signal on the phase shifter trace, reduce the loss of the RF signal on the phase shifter trace, and thus improve the beam quality and radiated power of the antenna.

[0010] It should be understood that the description in this section is not intended to identify key or essential features of the embodiments of the present invention, nor is it intended to limit the scope of the invention. Other features of the invention will become readily apparent from the following description. Attached Figure Description

[0011] To more clearly illustrate the technical solutions in the embodiments of the present invention, the accompanying drawings used in the description of the embodiments will be briefly introduced below. Obviously, the accompanying drawings described below are only some embodiments of the present invention. For those skilled in the art, other drawings can be obtained based on these drawings without creative effort.

[0012] Figure 1 This is a schematic diagram of a phase shifter provided in an embodiment of the present invention;

[0013] Figure 2 This is a schematic diagram of the structure of a phase-shifting unit provided in an embodiment of the present invention;

[0014] Figure 3 for Figure 2 A magnified structural diagram at point A;

[0015] Figure 4 for Figure 3 A schematic diagram of the cross-sectional structure along the B-B' direction;

[0016] Figure 5 for Figure 3 Schematic diagram of the structure of the grounding electrode layer;

[0017] Figure 6 An equivalent circuit diagram provided for an embodiment of the present invention;

[0018] Figure 7 This is a schematic diagram of the structure of a phase-shifting unit in related technologies;

[0019] Figure 8 This is a schematic diagram of another phase-shifting unit provided in an embodiment of the present invention;

[0020] Figure 9 for Figure 8 A magnified structural diagram at point D;

[0021] Figure 10 for Figure 9 Schematic diagram of the structure of the grounding electrode layer;

[0022] Figure 11 This is a partial structural schematic diagram of a phase-shifting unit provided in an embodiment of the present invention;

[0023] Figure 12 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention;

[0024] Figure 13 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention;

[0025] Figure 14 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention;

[0026] Figure 15 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention;

[0027] Figure 16 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention;

[0028] Figure 17 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention;

[0029] Figure 18 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention;

[0030] Figure 19 This is a schematic diagram of another phase-shifting unit provided in an embodiment of the present invention;

[0031] Figure 20 This is a schematic diagram of another phase shifter provided in an embodiment of the present invention;

[0032] Figure 21 A schematic diagram of an antenna structure provided in an embodiment of the present invention;

[0033] Figure 22 This is a schematic diagram of a partial cross-sectional structure of an antenna provided in an embodiment of the present invention. Detailed Implementation

[0034] To enable those skilled in the art to better understand the present invention, the technical solutions of the present invention will be clearly and completely described below with reference to the accompanying drawings of the embodiments of the present invention. Obviously, the described embodiments are only some embodiments of the present invention, and not all embodiments. Based on the embodiments of the present invention, all other embodiments obtained by those skilled in the art without creative effort should fall within the scope of protection of the present invention.

[0035] It should be noted that the terms "first," "second," etc., in the specification, claims, and accompanying drawings of this invention are used to distinguish similar objects and are not necessarily used to describe a specific order or sequence. It should be understood that such data can be interchanged where appropriate so that the embodiments of the invention described herein can be implemented in orders other than those illustrated or described herein. Furthermore, the terms "comprising" and "having," and any variations thereof, are intended to cover non-exclusive inclusion; for example, a process, method, system, product, or apparatus that comprises a series of steps or units is not necessarily limited to those steps or units explicitly listed, but may include other steps or units not explicitly listed or inherent to such processes, methods, products, or apparatus.

[0036] Figure 1 This is a schematic diagram of a phase shifter provided in an embodiment of the present invention. Figure 2 This is a schematic diagram of the structure of a phase-shifting unit provided in an embodiment of the present invention. Figure 3 for Figure 2 Enlarged structural diagram at point A Figure 4 for Figure 3 A schematic diagram of the cross-sectional structure along the B-B' direction. Figure 5 for Figure 3 A schematic diagram of the structure of the grounding electrode layer is shown below. Figures 1-5As shown, the phase shifter provided in this embodiment of the invention includes at least one phase shifting unit 10. The phase shifting unit 10 includes a phase shifter trace 101, an adjustable dielectric layer 102, and a ground electrode layer 103. The phase shifter trace 101 and the ground electrode layer 103 are disposed opposite to each other, and the adjustable dielectric layer 102 is located between the phase shifter trace 101 and the ground electrode layer 103. The phase shifter trace 101 includes a main trace 21 and at least one branch trace 22 that intersects and connects with the main trace 21. The ground electrode layer 103 includes at least one patterned region 30. The patterned region 30 includes at least two sub-cutout regions 301 arranged along a first direction X and a portion of the ground electrode layer 103 between adjacent sub-cutout regions 301. The first direction X is parallel to the extension direction of the main trace 21. The orthographic projection of the branch trace 22 on the plane where the ground electrode layer 103 is located is between the orthographic projections of the two adjacent sub-cutout areas 301 on the plane where the ground electrode layer 103 is located, and overlaps with the ground electrode layer 103 between the two adjacent sub-cutout areas 301.

[0037] Specifically, such as Figures 1-5 As shown, in order to achieve beamforming or scanning, a phase shifter contains multiple phase shifting units 10 arranged in an array.

[0038] In some embodiments, a phase shifter may also include a single phase shifting unit 10.

[0039] Figure 1 The illustration only uses a phase shifter with four phase shifting units 10 as an example. In other embodiments, those skilled in the art can set the number and layout of the phase shifting units 10 according to actual needs, and the embodiments of the present invention do not limit this.

[0040] Furthermore, each phase shifting unit 10 includes a phase shifter trace 101, which is used to transmit radio frequency signals, and the phase shifting unit 10 is used to implement the phase shifting function of the radio frequency signals transmitted on the phase shifter trace 101.

[0041] like Figure 1 As shown, when the phase shifter includes multiple phase shifting units 10 arranged in an array, it can simultaneously shift the phase of the radio frequency signals transmitted on multiple phase shifter traces 101 to control the phase of the radio frequency signals in each phase shifting unit 10. In turn, by controlling the phase difference between each phase shifting unit 10, the direction of the antenna radiation beam can be controlled, thereby achieving efficient beam scanning.

[0042] Continue to refer to Figures 1-5The phase shifting unit 10 is provided with a ground electrode layer 103 disposed opposite to the phase shifter trace 101. An adjustable dielectric layer 102 is disposed between the phase shifter trace 101 and the ground electrode layer 103. The radio frequency signal transmitted on the phase shifter trace 101 is transmitted in the adjustable dielectric layer 102 between the phase shifter trace 101 and the ground electrode layer 103.

[0043] The tunable dielectric layer 102 is composed of a dielectric material with an adjustable dielectric constant. The dielectric constant of the tunable dielectric layer 102 can be dynamically adjusted by applying different light or voltage.

[0044] Variations in the dielectric constant of the tunable dielectric layer 102 affect the propagation speed and phase of the radio frequency (RF) signal within the tunable dielectric layer 102. For example, a higher dielectric constant slows down the propagation speed of the RF signal, resulting in a greater phase delay; conversely, a lower dielectric constant allows the RF signal to propagate faster, reducing phase delay.

[0045] Therefore, by precisely controlling the dielectric constant of the adjustable dielectric layer 102, the radio frequency signal transmitted on the phase shifter trace 101 can be phase-shifted, thereby changing the phase of the radio frequency signal and realizing the phase shifting function of the radio frequency signal.

[0046] The specific material selection for the tunable dielectric layer 102 can be adapted based on factors such as operating frequency band, control method, process compatibility, and performance requirements. This embodiment of the invention does not limit the specific material composition of the tunable dielectric layer 102; any tunable dielectric material capable of dynamic control of the dielectric constant and suitable for phase shifter structures should be included within the scope of protection of this invention.

[0047] For example, such as Figures 1-5 As shown, the phase shifter is a liquid crystal phase shifter (LCPS). The adjustable dielectric layer 102 includes a liquid crystal layer 40. At this time, a driving voltage can be connected through the phase shifter trace 101 to form an electric field between the phase shifter trace 101 and the ground electrode layer 103. The electric field can drive the liquid crystal molecules 400 in the liquid crystal layer 40 to deflect, thereby changing the dielectric constant of the liquid crystal layer 40 and realizing the dynamic adjustment of the dielectric constant of the adjustable dielectric layer 102.

[0048] Alternatively, the driving voltage can be connected through other traces besides the phase shifter trace 101 to form an electric field between the phase shifter trace 101 and the ground electrode layer 103. This embodiment of the invention does not specifically limit this.

[0049] In some embodiments, the tunable dielectric layer 102 may also include a photodielectric layer. In this case, by introducing light of different intensities or wavelengths into the photodielectric layer, the structure and morphology of the material molecules in the photodielectric layer can be changed, thereby modulating the anisotropy of the physical properties of the photodielectric layer material and changing the dielectric constant of the photodielectric layer, thereby realizing the dynamic adjustment of the dielectric constant of the tunable dielectric layer 102.

[0050] The material of the photodielectric layer may include liquid crystal polymers, azo dyes, or azo polymers, etc., and the embodiments of the present invention do not specifically limit it.

[0051] In some embodiments, such as Figure 4 As shown, the phase shifter includes a first substrate 11 and a second substrate 12 disposed opposite to each other. The phase shifting unit 10 can be disposed between the first substrate 11 and the second substrate 12. The first substrate 11 and the second substrate 12 can provide stable mechanical support for the phase shifting unit 10, enhance the strength and durability of the phase shifter, and facilitate its manufacture.

[0052] For example, such as Figure 4 As shown, the ground electrode layer 103 in the phase shifting unit 10 can be fabricated on the first substrate 11, the phase shifter trace 101 can be fabricated on the second substrate 12, and the adjustable dielectric layer 102 is filled between the first substrate 11 and the second substrate 12.

[0053] In some embodiments, the first substrate 11 and the second substrate 12 may be made of glass substrates or printed circuit boards (PCBs) to ensure efficient signal transmission and provide good mechanical strength. Glass substrates can achieve high manufacturing precision and have high transparency, making the antenna more aesthetically pleasing. Printed circuit boards facilitate circuit layout. Printed circuit boards can be made of high-frequency substrates, allowing frequencies above 1 GHz. By using low-loss high-frequency substrates, the loss of radio frequency signals caused by the printed circuit board can be effectively reduced, improving the performance of the antenna. This embodiment of the invention does not impose specific limitations.

[0054] Furthermore, to meet the growing trend of miniaturization and thinning of modern electronic devices, the cell thickness of the phase shifter (i.e., the distance between the phase shifter trace 101 and the ground electrode layer 103) is typically designed to be very small. The inventors have discovered that under low cell thickness conditions, the phase shifter loss increases significantly, ultimately affecting the antenna's beam quality and radiated power. The main reasons include:

[0055] 1. When the cell thickness decreases, the electromagnetic field energy of the radio frequency signal is more concentrated in the narrow region between the phase shifter trace 101 and the ground electrode layer 103, causing the radio frequency current to be highly concentrated on the surface of the phase shifter trace 101 and the ground electrode layer 103, resulting in a significant increase in current density. According to Joule's law, conductor loss (ohmic loss) is proportional to the square of the current density, thus directly leading to a substantial increase in conductor loss.

[0056] 2. When the tunable dielectric layer 102 is a liquid crystal layer 40, the anchoring effect of the first substrate 11 and the second substrate 12 on the liquid crystal molecules 400 is enhanced in the thinner liquid crystal layer 40, which restricts the free rotation ability of the liquid crystal molecules 400 under the applied electric field, resulting in a smaller range of variation of its effective dielectric constant. In order to achieve the same phase shift, it is necessary to extend the length of the phase shifter trace 101, thereby accumulating more transmission loss.

[0057] Based on the above-mentioned technical problems, in this embodiment, as follows: Figures 1-5 As shown, the phase shifter trace 101 includes a main trace 21, which is the main part of the phase shifter trace 101 that realizes signal transmission and phase adjustment functions. The main trace 21 usually extends along a certain direction (such as the first direction X) and has a continuous and through-type trace shape. It can be a straight line, a broken line, a spiral, or other compact layout to adapt to different spatial constraints.

[0058] At least one patterned region 30 is provided on the ground electrode layer 103. Each patterned region 30 includes at least two sub-cutout regions 301. The sub-cutout regions 301 refer to the opening structures formed on the ground electrode layer 103 by etching, laser drilling or other micro-machining processes.

[0059] Along the direction perpendicular to the plane of the ground electrode layer 103, the sub-cutout region 301 overlaps with the main trace 21. The sub-cutout region 301 and the overlapping portion of the main trace 21 can constitute a Defected Ground Structure (DGS). By setting the sub-cutout region 301 on the ground electrode layer 103, the return current on the ground electrode layer 103 cannot flow along its original path but is forced to bypass the sub-cutout region 301, thereby changing the return path of the return current on the ground electrode layer 103 and making the actual path of the return current longer. Since inductance is proportional to the path length of the current, setting the defected ground structure is equivalent to connecting an equivalent inductor in series on the phase shifter trace 101, thus increasing the distributed inductance on the phase shifter trace 101.

[0060] Furthermore, in the patterned region 30, at least a portion of the ground electrode layer 103 is retained between adjacent sub-cutout regions 301. Laterally, branch traces 22 are correspondingly led out from the main trace 21. These branch traces 22 are led out from one or both sides of the main trace 21 in a non-parallel manner (e.g., perpendicular or approximately perpendicular), and form an electrical connection with the main trace 21 at the connection point, forming a cross-shaped or similar intersecting structure on the plane. The main trace 21 and the branch traces 22 can be fabricated on the same conductor layer, formed simultaneously through a single photolithography and etching process.

[0061] Along a direction perpendicular to the plane of the ground electrode layer 103, the stub trace 22 overlaps with the ground electrode layer 103 between adjacent sub-cutout areas 301, forming an open-ended short stub (SUB) structure between the stub trace 22 and the overlapping portion of the ground electrode layer 103. Specifically, as shown... Figures 1-5 As shown, along the direction perpendicular to the extension direction of the phase shifter trace 101, or in other words, along the direction perpendicular to the direction of radio frequency signal transmission on the phase shifter trace 101 (i.e., the second direction Y), the length of the stub trace 22 is greater than the width of the main trace 21, thereby introducing an additional conductor stub on at least one side of the main trace 21. This additional conductor stub can increase the capacitive coupling area between the phase shifter trace 101 and the ground electrode layer 103. Therefore, setting an open-circuit short stub structure in the phase shifter trace 101 is equivalent to introducing a parallel capacitor branch on the phase shifter trace 101, which can increase the distributed capacitance of the phase shifter trace 101.

[0062] Figure 6 An equivalent circuit diagram is provided for an embodiment of the present invention, such as... Figures 1-6 As shown, the defective ground structure can be equivalent to adding a series equivalent inductor 30L to the phase shifter trace 101, and the open-circuit stub structure can be equivalent to adding a parallel equivalent capacitor 30C to the phase shifter trace 101. In the patterned region 30, at least two sub-cutout regions 301 forming the defective ground structure are arranged along the first direction X (i.e., the extension direction of the main trace 21). At the same time, the open-circuit stub structure is located between two adjacent sub-cutout regions 301. This local structure exhibits a "series inductor-parallel capacitor-series inductor" structure in terms of electromagnetic behavior.

[0063] Radio frequency signals can satisfy the formula during transmission. ;

[0064] in, It is the phase velocity, which is the speed at which the radio frequency signal propagates in the phase shifter trace 101.

[0065] Distributed inductance refers to the inductance value per unit length.

[0066] Distributed capacitance refers to the capacitance per unit length.

[0067] It is the frequency of the radio frequency signal.

[0068] It is the wavelength of the radio frequency signal.

[0069] Therefore, by setting up a defective ground structure and an open-circuit short stub structure, the equivalent inductance 30L and equivalent capacitance 30C are introduced on the phase shifter trace 101, thereby increasing the distributed inductance on the phase shifter trace 101. and distributed capacitance Distributed inductance and distributed capacitance Increasing the phase velocity can decrease the phase velocity. To achieve the slow-wave effect, at a frequency... Under the condition of invariance, wavelength This will also reduce the phase change, thus achieving the same or greater phase change within a shorter physical length. This allows the length of the phase shifter trace 101 to be significantly shortened, thereby reducing the transmission path length of the radio frequency signal on the phase shifter trace 101, reducing the loss of the radio frequency signal on the phase shifter trace 101, and thus improving the beam quality and radiation power of the antenna.

[0070] On the other hand, by setting up defective ground structures and open-circuit short stub structures, the distributed inductance on the phase shifter trace 101 is increased. and distributed capacitance Decrease phase velocity This achieves the slow-wave effect and can significantly increase the equivalent electrical length of a signal without changing its physical length.

[0071] Specifically, electric length is defined as: ;

[0072] in, This is the physical length of the phase shifter trace 101.

[0073] The phase shift degree Δφ of the phase shifter is proportional to the electrical length, satisfying the formula... ,in, is the phase constant.

[0074] Therefore, at the same physical length Below, the reduction is achieved through a "series inductor-parallel capacitor-series inductor" structure. This increases the electrical length, thereby achieving a greater phase shift Δφ.

[0075] Furthermore, the performance of the phase shifter can be evaluated by the figure of merit (FoM), which satisfies the formula FoM=ΔΦb,max / ILmax.

[0076] Wherein, ΔΦb,max represents the phase shift degree of the phase shifter, which is the maximum phase change that the phase shifter can achieve, usually expressed in degrees (°) or radians (rad).

[0077] ILmax represents the maximum insertion loss of the phase shifter. Insertion loss refers to the power loss of a signal when it passes through the phase shifter, and is usually measured in decibels (dB).

[0078] As mentioned above, in this embodiment of the invention, by setting a defective ground structure and a parallel stub structure, the same or greater phase change can be achieved within a shorter physical length, which can significantly shorten the length of the phase shifter trace 101, reduce the loss of radio frequency signals on the phase shifter trace 101, thus increasing the maximum phase offset ΔΦb,max of the phase shifter and reducing the maximum insertion loss ILmax of the phase shifter, achieving a higher quality factor FoM, and improving the overall performance of the phase shifter.

[0079] Figure 7 As shown in Table 1, the phase shifter provided in this application achieves a maximum phase shift of 235.5°, which is significantly higher than the 76.21° of phase shifters in related technologies (e.g., ...). Figure 7 The phase shifter shown indicates that it has a stronger phase control capability.

[0080] Taking into account both phase shift and loss, the phase shifter provided in this application achieves a FOM of 30.78, which is far superior to the 17.84 of phase shifters in related technologies, representing an improvement of over 70%.

[0081] Table 1. Performance Comparison of Phase Shifter in this Application and Phase Shifters in Related Technologies

[0082]

[0083] Furthermore, in this embodiment of the invention, only the pattern shape of the phase shifter trace 101 needs to be changed, and a corresponding sub-cutout area 301 is set on the ground electrode layer 103. No additional processing steps are required during manufacturing, making the manufacturing process simple and easy to implement.

[0084] In summary, the phase shifter provided in the embodiments of the present invention includes a main trace and at least one branch trace that intersects and connects with the main trace. The ground electrode layer includes at least one patterned region. The patterned region includes at least two sub-cutout regions arranged along a first direction and a portion of the ground electrode layer between adjacent sub-cutout regions. The first direction is parallel to the extension direction of the main trace. The sub-cutout region 301 and the overlapping main trace portion constitute a defective ground structure, introducing equivalent inductance into the phase shifter trace. The orthogonal projection of the stub trace onto the plane of the ground electrode layer is located between two adjacent sub-cutout regions and overlaps with the ground electrode layer between two adjacent sub-cutout regions, forming an open-circuit short stub structure, thereby introducing equivalent capacitance into the phase shifter trace. This increases the distributed inductance and distributed capacitance on the phase shifter trace, reduces the phase velocity and wavelength, and achieves a slow wave effect. As a result, the same or greater phase change can be achieved within a shorter physical length, which can significantly shorten the length of the phase shifter trace, reduce the transmission path length of the RF signal on the phase shifter trace, reduce the loss of the RF signal on the phase shifter trace, and thus improve the beam quality and radiated power of the antenna.

[0085] Figure 8 This is a schematic diagram of another phase-shifting unit provided in an embodiment of the present invention. Figure 9 for Figure 8 Enlarged structural diagram at point D Figure 10 for Figure 9 A schematic diagram of the structure of the grounding electrode layer is shown below. Figures 8-10 As shown, optionally, two adjacent sub-cutout regions 301 are connected, and the orthographic projection of the connected region 302 on the plane of the ground electrode layer 103 overlaps with the orthographic projection of the intersection region 23 of the main trace 21 and the branch trace 22 on the plane of the ground electrode layer 103. The ground electrode layer 103 between two adjacent sub-cutout regions 301 includes two spacers 303, which are located on both sides of the connected region 302 along the second direction Y, which is parallel to the extension direction of the branch trace 22.

[0086] Specifically, such as Figures 8-10 As shown, in the patterned area 30, two adjacent sub-cutout areas 301 are connected to each other through a connecting area 302, thereby forming an overall "H-shaped" cutout structure on the ground electrode layer 103.

[0087] The main trace 21 and the branch trace 22 form an intersection region 23 in a local area where they connect or intersect on the plane. Along the direction perpendicular to the plane where the ground electrode layer 103 is located, the connecting region 302 overlaps with the intersection region 23 of the main trace 21 and the branch trace 22. This design allows the ground electrode layer 103 to have a hollow channel (i.e., connecting region 302) running along the first direction X at the connection point of the main trace 21 and the branch trace 22 (i.e., connecting region 302), which helps to adjust the equivalent inductance of this local area.

[0088] Furthermore, along the second direction Y, that is, the extension direction of the stub trace 22 (such as the extension direction perpendicular to the main trace 21), two spacers 303 between two adjacent sub-cutout regions 301 are located on both sides of the connecting region 302, thereby retaining two uncut ground electrode layers 103 (spacers 303) on both sides of the connecting region 302. These two spacers 303 form a strong capacitive coupling with the stub trace 22, providing the required parallel equivalent capacitance.

[0089] This embodiment, compared to two completely isolated sub-cutout regions 301, offers additional design freedom and performance optimization potential. Specifically, the width (along the second direction Y) and length (along the first direction X) of the connected region 302 become new adjustable variables. Adjusting the size of this region allows for fine-tuning of the coupling strength between the two spacers 303, as well as the resonant characteristics of the entire defect structure. This enables more flexible fine-tuning of the impedance and frequency response of the entire "series inductor-parallel capacitor-series inductor" structure to achieve optimal impedance matching and bandwidth performance.

[0090] Optional, such as Figures 8-10 As shown, the two spacer portions 303 are symmetrically arranged relative to the connected region 302.

[0091] Specifically, such as Figures 8-10 As shown, the two partitions 303 located on both sides of the connected region 302 are arranged in a mirror-symmetric layout along the second direction Y (i.e., the direction parallel to the extension of the branch line 22). At this time, the two partitions 303 have the same geometry, that is, the two partitions 303 have the same geometric outline; the two partitions 303 have the same size, that is, the key dimensional parameters such as the area, length and width of the two partitions 303 are consistent; the relative positions of the two partitions 303 are symmetrical, that is, the two partitions 303 are symmetrically distributed about the central axis of the connected region 302.

[0092] With this configuration, when the radio frequency current flows in the ground electrode layer 103 and encounters the symmetrical defect ground structure, the current is forced to shunt and circumvent two symmetrical paths (i.e., flowing through the outer sides of the two spacers 303). The symmetrical geometry ensures that the current amplitude and phase of the current shunt to both sides are highly consistent. This uniform current distribution helps to produce a predictable and stable equivalent inductance value and reduces additional losses and parasitic radiation caused by uneven current distribution.

[0093] Meanwhile, the coupling electric field between the branch trace 22 and the two spacers 303 is symmetrical, which can ensure that the electric field lines of the capacitor are evenly distributed, making the performance of the formed equivalent capacitor C more stable and reducing the sensitivity to process fluctuations (such as photolithography alignment deviations).

[0094] Furthermore, the aforementioned symmetrical design helps to achieve a larger capacitive coupling area within a limited space, thereby achieving a larger equivalent capacitance. This helps to reduce the space occupied by the phase shifter trace 101, improve the integration of the phase shifter, and achieve miniaturization.

[0095] Figure 11 This is a partial structural diagram of a phase-shifting unit provided in an embodiment of the present invention, as shown below. Figure 11 As shown, optionally, the length D1 of the sub-cutout area 301 along the first direction X is greater than or equal to the length D2 along the second direction Y, where the second direction Y is parallel to the extension direction of the branch line 22.

[0096] If the sub-cutout area 301 is too wide in the second direction Y (i.e., D2 is very large), in order to avoid the patterned areas 30 of adjacent phase shifting units 10 (especially the sub-cutout area 301) being too close or overlapping in the second direction Y, thereby causing unnecessary electromagnetic coupling between phase shifting units 10 or reducing the mechanical / electrical integrity of the ground electrode layer 103, it is necessary to increase the center distance of adjacent phase shifting units 10 in the second direction Y.

[0097] In this embodiment, as Figure 11 As shown, the length D2 of the sub-hollow area 301 along the extension direction of the branch line 22 is not greater than its length D1 along the extension direction of the main line 21, that is, D1≥D2.

[0098] By limiting the size of D2 (making it ≤ D1), the lateral space occupied by the sub-cutout area 301 in the second direction Y can be significantly reduced, so that the ground electrode layer 103 of adjacent phase shifting units 10 can retain a wider and more stable metal area under the same center distance of phase shifting units 10; or, under the premise of meeting the same isolation requirements, the center distance of phase shifting units 10 can be reduced, thereby increasing the arrangement density of phase shifting units 10.

[0099] Meanwhile, the equivalent inductance introduced by the sub-cutout region 301 mainly stems from its forced grounding current to bypass the current path. When the cutout region extends along the main current path (first direction X) (where D1 is larger), the current path is longer, which helps to achieve a higher inductance within the limited lateral space (the second direction Y dimension D2 is limited). This allows the inductance effect to be more concentrated in the direction of extension of the main trace 21 and more coordinated with the direction of RF signal transmission, contributing to a more defined distribution parameter.

[0100] Figure 12 This is a partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention, as shown below. Figure 12 As shown, optionally, two adjacent sub-cutout regions 301 are connected, and the orthographic projection of the connected region 302 on the plane of the ground electrode layer 103 overlaps with the orthographic projection of the intersection region 23 of the main trace 21 and the branch trace 22 on the plane of the ground electrode layer 103. The ground electrode layer 103 between two adjacent sub-cutout regions 302 includes two spacer portions 303, which are located on both sides of the connected region 302 along the second direction Y. The length D3 of the spacer portion 303 along the first direction X is greater than or equal to the length D4 along the second direction Y.

[0101] The specific structure and effects of the connected region 302 and the spacer 303 can be referred to in any of the above embodiments, and will not be repeated here.

[0102] In this embodiment, the length of each interval 303 along the first direction X (i.e., the direction parallel to the extension of the main line 21) is denoted as D3, and the length along the second direction Y is denoted as D4, and D3≥D4 is satisfied.

[0103] The length D3 of the spacer 303 along the first direction X directly determines the length of its overlap with the stub trace 22 in the first direction X. The capacitance value is proportional to the overlap area. By increasing the length D3 of the spacer 303 along the first direction X (not less than D4), the overlap area between the spacer 303 and the stub trace 22 can be significantly increased without increasing (or even decreasing) the lateral area occupied by the spacer 303 (determined by D4), thus achieving a larger capacitance efficiently within a compact lateral space.

[0104] Meanwhile, the spacer 303 is designed to extend along the first direction X, so that the coupling electric field between it and the stub trace 22 is more concentrated in the same direction as the radio frequency signal transmission, which is conducive to forming more controllable and stable distributed capacitance parameters.

[0105] In addition, the shape of the spacer 303 extending along the first direction X makes the grounding current path flowing through the edge of the spacer 303 smoother, which helps to reduce the additional losses caused by current congestion.

[0106] Optional, such asFigure 9 and Figure 10 As shown, the length D5 of the sub-hollow area 301 along the first direction X is less than the length D6 along the second direction Y, and the second direction Y is parallel to the extension direction of the branch line 22.

[0107] Specifically, such as Figure 9 and Figure 10 As shown, the length of the sub-cutout region 301 along the first direction X (i.e., the direction parallel to the main routing line 21) is denoted as D5, and the length along the second direction Y (i.e., the direction parallel to the branch routing line 22, which may be perpendicular to the first direction X) is denoted as D6. In this embodiment, D5 < D6, that is, the size of the sub-cutout region 301 in the second direction Y is greater than its size in the first direction X, and the whole has a shape that extends laterally (perpendicular to the direction of radio frequency signal propagation).

[0108] Each sub-cutout region 301 can be equivalent to an inductor. Within the same main trace length 21 (along the first direction X), a wider, shorter cutout (smaller D5) allows for a greater number of sub-cutout regions 301 to be arranged in the first direction X. Since the phase shift is proportional to the electrical length, and the increase in electrical length stems from the slow wave effect introduced by each inductor and capacitor, arranging a greater number of sub-cutout regions 301 within a fixed physical length is equivalent to connecting more inductors in series. This allows for a greater overall phase shift within a shorter physical length, significantly shortening the length of the phase shifter trace 101. This reduces the transmission path length of the RF signal on the phase shifter trace, lowers the loss of the RF signal on the phase shifter trace, and thus improves the antenna's beam quality and radiated power.

[0109] Meanwhile, due to the larger D6, the sub-cutout region 301 has a stronger lateral blocking effect on the RF current in the second direction Y. When the RF current attempts to find the lowest impedance path in the lateral direction (second direction Y) of the ground electrode layer 103, it will encounter a wider obstacle, forcing the RF current to travel further to both sides of the sub-cutout region 301, which is equivalent to increasing the current path length of each equivalent inductor, thereby obtaining a higher inductance.

[0110] Optional, such as Figure 3 As shown, the orthographic projections of two adjacent sub-cutout regions 301 onto the plane of the ground electrode layer 103 are symmetrically arranged with respect to the central axis 51 of the orthographic projection of the branch trace 22 onto the plane of the ground electrode layer 103.

[0111] Specifically, such as Figure 3As shown, each patterned region 30 includes at least one pair of sub-cutout regions 301. Based on the orthographic projection of the branch trace 22 onto the plane of the ground electrode layer 103, a central axis 51 is defined on this projection pattern along its extension direction (i.e., the second direction Y). This central axis 51 represents the center position of the branch trace 22 on the plane. Adjacent sub-cutout regions 301 are mirror-symmetrical about the central axis 51 of the aforementioned projection of the branch trace 22.

[0112] At this time, the shapes of the two sub-cutout areas 301 are mirror images of each other, the distances from the two sub-cutout areas 301 to the central axis 51 are equal, and the central axis 51 passes through the central area between the two sub-cutout areas 301.

[0113] The symmetrical design described above helps to maintain the uniformity of current density distribution during radio frequency signal propagation, reduce local hot spots or overheating, and improve the reliability and stability of the phase shifter.

[0114] Meanwhile, by adopting the above symmetrical design, the sub-cutout area 301 can be designed to extend its size to both sides as much as possible within the limited horizontal (second direction Y) layout width. This helps to achieve a larger sub-cutout area 301 within a limited space, thereby achieving a larger equivalent inductance. This is beneficial to reduce the space occupied by the phase shifter trace 101, improve the integration of the phase shifter, and achieve miniaturization design.

[0115] In addition, the symmetrical design facilitates patterned processing using standardized templates, reducing manufacturing complexity, improving production efficiency, and also helping to increase the yield rate.

[0116] Optional, such as Figure 9 As shown, the same branch line 22 is symmetrically arranged with respect to the central axis 52 of the main line 21.

[0117] Specifically, such as Figure 9 As shown, based on the extension path of the main route 21 near or in the intersection area 23, a geometric center line along the first direction X (i.e. its own extension direction) is defined, which is called the central axis 52 of the main route 21.

[0118] In this embodiment, the overall structure of the branch lines 22 branching off from the main line 21 is mirror-symmetrical with respect to the central axis 52 of the main line 21. At this time, the branch lines 22 are designed to extend outward simultaneously and symmetrically from both sides of the main line 21, and their overall layout is symmetrical about the central axis 52. The branches on the left and right sides are completely symmetrical in shape, size and position.

[0119] With this configuration, the radio frequency signal is transmitted in the main trace 21. When it reaches the intersection region 23, the current is shunted to the stub trace 22. The symmetrical stub structure ensures that the current is evenly and equally distributed to both branches. This balanced current shunting avoids the excessively high local current density that may result from current concentration on one side, thereby helping to reduce the resulting conductor losses. At the same time, it can also suppress unexpected common-mode currents or asymmetric field modes that may be excited by unbalanced current shunting, reducing parasitic radiation.

[0120] Meanwhile, for the formation of parallel capacitors, the capacitance value is proportional to the overlap area of ​​the upper and lower plates (stub trace 22 and ground plane connection 302). The symmetrical stub trace 22 design allows it to fully utilize the available width to extend in the second direction Y on both sides adjacent to the main trace 21. Compared with asymmetrical stubs that extend only on one side, the symmetrical design can increase the effective capacitance area without increasing the overall layout width on both sides of the main trace 21, thereby achieving a larger equivalent capacitance. This helps to reduce the space occupied by the phase shifter trace 101, improve the integration of the phase shifter, and achieve miniaturization design.

[0121] Optional, such as Figure 9 As shown, the same sub-cutout area 301 is symmetrically arranged with respect to the central axis of the orthographic projection of the main trace 21 onto the plane where the ground electrode layer 103 is located.

[0122] Specifically, such as Figure 9 As shown, the orthographic projection of the main trace 21 onto the plane of the ground electrode layer 103 is used as the geometric reference. On this projection pattern, a geometric center line along its extension direction (first direction X) is defined as the central axis 53 of the projection of the main trace 21. The central axis 53 represents the center position of the projection of the main trace 21 onto the ground electrode layer 103.

[0123] like Figure 9 As shown, the geometry and dimensional parameters of a single sub-cutout region 301 are mirror-symmetrical about the central axis 53 of the orthographic projection of the main trace 21 onto the ground electrode layer 103. At this time, the outline, size, and relative position of the sub-cutout region 301 are all designed around the central axis 52 of the main trace 21, and its axis of symmetry coincides with the central axis 23 of the projection of the main trace 21.

[0124] The symmetrical design described above helps to maintain the uniformity of current density distribution during radio frequency signal propagation, reduce local hot spots or overheating, and improve the reliability and stability of the phase shifter.

[0125] Meanwhile, by adopting the above symmetrical design, the sub-cutout area 301 can be designed to extend its size to both sides as much as possible within the limited horizontal (second direction Y) layout width. This helps to achieve a larger sub-cutout area 301 within a limited space, thereby achieving a larger equivalent inductance. This is beneficial to reduce the space occupied by the phase shifter trace 101, improve the integration of the phase shifter, and achieve miniaturization design.

[0126] Optional, such as Figure 9 As shown, the length D7 of the branch line 22 along the second direction Y is greater than the length D6 of the sub-hollow area 301 along the second direction Y, and the second direction Y is parallel to the extension direction of the branch line 22.

[0127] Specifically, such as Figure 9 As shown, the length D7 of the branch line 22 in its extension direction (second direction Y) is greater than the length D6 of the sub-hollow area 301 in the same direction (second direction Y), that is, D7>D6.

[0128] With this configuration, the length D7 of the stub trace 22 along the second direction Y is larger, which can increase the overlap area between it and the ground electrode layer 103, thereby enhancing the capacitive coupling between the stub trace 22 and the ground electrode layer 103, forming a larger equivalent capacitance, which helps to achieve a more significant slow wave effect. This allows for a greater total phase shift within a shorter physical length, significantly shortening the length of the phase shifter trace 101, reducing the transmission path length of the radio frequency signal on the phase shifter trace, reducing the loss of the radio frequency signal on the phase shifter trace, and thus improving the beam quality and radiated power of the antenna.

[0129] Figure 13 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention is shown below. Figure 13 As shown, optionally, the stub trace 22 includes a first portion 221 and a second portion 222 that are interconnected. The orthographic projection of the first portion 221 onto the plane of the ground electrode layer 103 is located between adjacent sub-cutout regions 301. The second portion 222 is located on at least one side of the first portion 221 along the second direction Y. The second direction Y is parallel to the extension direction of the stub trace 22. The length L1 of the second portion 222 along the first direction X is greater than or equal to the length L3 of the first portion 221 along the first direction X.

[0130] Specifically, such as Figure 13 As shown, the branch trace 22 portion between adjacent sub-cutout regions 301, whose orthogonal projection on the plane where the ground electrode layer 103 is located, is the first section 221. The second section 222 is formed by connecting to the end of the first section 221 and extending outward along the second direction Y (the extension direction of the branch trace 22) on one or both sides of the first section 221.

[0131] In this embodiment, the length L1 of the second portion 222 along the first direction X (i.e., the direction parallel to the extension of the main trace 21) is greater than the length L3 of the first portion 221 along the same direction (first direction X). This makes the length L1 of the second portion 222 along the first direction X larger, which can increase the overlap area between it and the ground electrode layer 103, thereby enhancing the capacitive coupling between the stub trace 22 and the ground electrode layer 103, forming a larger effective capacitance value. This helps to achieve a more significant slow wave effect, which is beneficial to shorten the length of the phase shifter trace 101, reduce the transmission path length of the radio frequency signal on the phase shifter trace, reduce the loss of the radio frequency signal on the phase shifter trace, and thus improve the beam quality and radiation power of the antenna.

[0132] Figure 14 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention is shown below. Figure 14 As shown, optionally, the second portion 222 of the branch line 22 is located on one side of the first portion 221 along the second direction Y.

[0133] Specifically, such as Figure 14 As shown, the second branch 222 is only provided on one side of the first branch 221 along the second direction Y, that is, the second branch 222 extends from the first branch 221 along the second direction Y to one side, forming an asymmetrical branch structure.

[0134] Compared to a symmetrical arrangement on both sides, setting a second section 222 on one side can effectively reduce the total width occupied by the branch traces 22 in the second direction Y, which is beneficial to reduce the spacing of the phase shifting units 10 in a high-density phased array and improve the overall integration.

[0135] In some embodiments, such as in a phased array antenna, arranging all the second portions 222 toward the side away from the adjacent phase-shifting unit 10 can effectively reduce cross-unit edge field coupling, reduce inter-channel crosstalk, and improve beam scanning accuracy, but is not limited to this.

[0136] Figure 15 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention is shown below. Figure 15 As shown, optionally, the second portion 222 of the branch line 22 is located on the same side of the first portion 221 along the second direction Y.

[0137] Specifically, such as Figure 15 As shown, the second portions 222 of different branch lines 22 all extend outward from the first portion 221 along the second direction Y to the same side. By concentrating the second portions 222 of all branch lines 22 on the same side of the first portion 221, the branch lines 22 can be optimized by uniform design parameters (such as length and width) to ensure that the performance of each branch line 22 is consistent.

[0138] Figure 16 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention is shown below. Figure 16 As shown, optionally, the second portion 222 of the adjacent branch line 22 is located on a different side of the first portion 221 along the second direction Y.

[0139] Specifically, such as Figure 16 As shown, the second portions 222 of two adjacent branch lines 22 are alternately located on the opposite side of their respective first portions 221. For example, if the second portion 222 of the first branch line 22 is located to the left of its first portion 221, then the second portion 222 of the next adjacent branch line 22 is located to the right of its first portion 221.

[0140] By staggering the second portion 222 of the adjacent branch traces 22 to different sides of the first portion 221, the electric field distribution in the second direction Y can be effectively balanced, which helps to make the electric field distribution more uniform, avoid excessive concentration of local electric field, thereby reducing the peak electric field intensity, reducing nonlinear loss, and preventing non-uniformity and reflection of radio frequency signals during transmission.

[0141] Optional, such as Figure 13 As shown, the second part 222 of the branch line 22 is located on both sides of the first part 221 along the second direction Y, and the branch line 22 is in the shape of an I-beam.

[0142] Specifically, such as Figure 13 As shown, the first section 221 extends along the second direction Y (usually perpendicular to the main line 21), and the two second sections 222 extend from both ends of the first section 221 along the second direction Y to both sides. Thus, the overall planar outline of the branch line 22 presents an "I" shape, with a composite geometric configuration of a central horizontal section (first section 221) and two side vertical sections (second section 222).

[0143] The second section 222 on both sides significantly increases the effective overlap area between the stub trace 22 and the ground electrode layer 103, thereby introducing a larger equivalent parallel capacitance, which helps to achieve a more significant slow wave effect. This allows for a greater total phase shift within a shorter physical length, significantly shortening the length of the phase shifter trace 101, reducing the transmission path length of the radio frequency signal on the phase shifter trace, reducing the loss of the radio frequency signal on the phase shifter trace, and thus improving the beam quality and radiated power of the antenna.

[0144] Meanwhile, the "I"-shaped structure is symmetrical about the main trace 21, which helps to maintain the balanced distribution of the electromagnetic field in the second direction Y, avoid characteristic impedance mismatch or common mode current, and reduce reflection loss and radiation interference.

[0145] In some embodiments, such as Figure 13As shown, the second section 222 is rectangular, which makes the branch wiring 22 present a standard "I" shaped structure.

[0146] The shape of the second part 222 is not limited to a rectangle, and can be designed according to specific performance optimization objectives (such as electric field distribution, frequency response) or process characteristics.

[0147] For example, the second section 222 may be circular or elliptical in shape. This shape has no sharp corners, which helps to further reduce the current accumulation effect and edge radiation at the corners. In high-frequency applications, it can have better loss characteristics. At this time, the stub trace 22 is generally "dumbbell-shaped" or "double round head-shaped", but it is not limited to this.

[0148] In some embodiments, the second portion 222 may be hexagonal, octagonal or other polygonal, and by chamfering, the edge electric field distribution can be improved while approaching rectangular area efficiency.

[0149] In some embodiments, regardless of the specific shape of the second portion 222, the second portions 222 located on both sides of the first portion 221 preferably adopt the same shape and are arranged in strict mirror symmetry with respect to the first portion 221. This symmetry can ensure uniform current distribution and balanced capacitive coupling.

[0150] Optional, such as Figure 13 As shown, the length of the second part 222 in the first direction X is L1, and the total length of the grounding electrode layer 103 between the two adjacent sub-cutout regions 301 and the two sub-cutout regions 301 in the first direction X is L2, where L1≤L2.

[0151] Specifically, such as Figure 13 As shown, the length of the second portion 222 in the first direction X is L1, and the total length of the two adjacent sub-cutout regions 301 corresponding to it and the grounding electrode layer 103 (i.e., the spacer 303 or the connecting region 302) between the two sub-cutout regions 301 in the first direction X is L2. Here, L2 can be understood as the total projected length along the first direction X (i.e., the direction parallel to the main trace 21), from the starting edge of the first sub-cutout region 301 to the ending edge of the second sub-cutout region 301. Specifically, it includes the length of the first sub-cutout region 301 in the first direction X, the length of the grounding electrode layer 103 (such as the spacer 303 or the connecting region 302) retained between the two sub-cutout regions 301 in the first direction X, and the length of the second sub-cutout region 301 in the first direction X.

[0152] In this way, by setting the length L1 of the second portion 222 in the first direction X to be no greater than the total length L2 of the ground electrode layer 103 between the two sub-cutout regions 301 in the first direction X, it is ensured that the dominant region of capacitive coupling is located in the middle of the lateral range of the effective patterned region 30, and the performance is predictable.

[0153] Meanwhile, limiting L1≤L2 ensures that each formed capacitor is essentially constrained within the lateral range of its corresponding patterned region 30, reducing mutual influence with adjacent patterned regions 30 through near-field coupling and lowering crosstalk between adjacent patterned regions 30.

[0154] Figure 17 A partial structural schematic diagram of another phase-shifting unit provided in an embodiment of the present invention is shown below. Figure 17 As shown, optionally, the length D7 of the branch line 22 along the second direction Y is less than or equal to the length D6 of the sub-cutout area 301 along the second direction Y, and the second direction Y is parallel to the extension direction of the branch line 22.

[0155] Specifically, when the length D7 of the branch trace 22 is greater than the length D6 of the sub-cutout area 301 (D7>D6), the end of the branch trace 22 will extend beyond the area where the sub-cutout area 301 is located. In order to ensure that there is no short circuit or strong coupling between the branch traces 22 of adjacent phase shifting units 10, a safety gap needs to be reserved between their phase shifting units 10, which will increase the center distance between adjacent phase shifting units 10.

[0156] In this embodiment, as Figure 17 As shown, the length D7 of the branch trace 22 in its extension direction (second direction Y) is set to be less than or equal to the length D6 of the sub-cutout area 301 in the same direction (second direction Y). By limiting D7≤D6, it is ensured that all parts of the branch trace 22 are located between the sub-cutout areas 301 and do not extend outward. This is beneficial for arranging the phase shifting unit 10 more closely, improving the integration of the phase shifter, and realizing miniaturized design.

[0157] Optionally, the number of sub-cutout areas 301 in the patterned area 30 can be 2 or 3.

[0158] Specifically, such as Figure 10 As shown, the patterned region 30 includes two sub-cutout regions 301 arranged along the first direction X. There is a connecting region 302 between two adjacent sub-cutout regions 301. At this time, the overall cutout of the patterned region 30 (the two sub-cutout regions 301 and the connecting region 302 between them) is in the shape of "I". It and the phase shifter trace 101 form a "series inductor-parallel capacitor-series inductor" structure, which can meet the phase shift requirements of most phase shifters. The structure is simple and easy to model and manufacture.

[0159] Figure 18 FIG. is a partial structural schematic diagram of another phase shifter unit provided by an embodiment of the present invention. As Figure 18 shown, the patterned region 30 includes three sub-hollow regions 301 arranged in sequence along the first direction X. There is a communication region 302 between two adjacent sub-hollow regions 301. At this time, the overall hollowing of the patterned region 30 (the three sub-hollow regions 301 and the two communication regions 302 between them) is in the shape of a "king character", and it forms a structure of "series inductor - parallel capacitor - series inductor - parallel capacitor - series inductor" with the phase shifter trace 101, which can provide a stronger slow wave effect, so that a larger phase shift can be achieved within a shorter length, and a richer frequency response characteristic can be shown, providing a greater degree of freedom for finer tuning in terms of phase shift, bandwidth, out-of-band rejection, etc.

[0160] Figure 19 FIG. is a structural schematic diagram of another phase shifter unit provided by an embodiment of the present invention. As Figures 1-19 shown, optionally, the stub trace 22 and its corresponding overlapping patterned region 30 form a transmission sub-unit 60. In the same phase shifter unit 10, the transmission sub-units 60 are arranged along the winding direction of the main trace 21.

[0161] Specifically, as Figures 1-19 shown, a patterned region 30 of the ground electrode layer 103 and the corresponding part of the phase shifter trace 101 in precise alignment are regarded as a basic functional unit for realizing the slow wave effect, and is called a transmission sub-unit 60. Each transmission sub-unit 60 is responsible for introducing a specific amount of inductance and capacitance, and can independently realize the slow wave function.

[0162] Inside a phase shifter unit 10, its main trace 21 can be in a meandering shape such as a serpentine line or a spiral line to increase the length within a limited area. The winding direction is the path direction in which the main trace 21 meanders forward.

[0163] In this embodiment, multiple transmission sub-units 60 are distributed along the meandering path of the main trace 21 in sequence and at intervals, and their arrangement direction is consistent with the extension trajectory of the main trace 21.

[0164] Among them, the transmission sub-units 60 are loaded periodically or quasi-periodically along the radio frequency signal transmission direction (i.e., the winding direction) to ensure that the phase shift contributions introduced by each transmission sub-unit 60 can play a role coherently and cumulatively along the signal path, avoiding the cancellation of phase perturbations introduced by chaotic arrangement or the generation of unnecessary reflections, which is beneficial to improving the overall efficiency.

[0165] Meanwhile, when the transmission sub-units 60 are arranged uniformly or according to a specific pattern along the winding direction, the impedance of the main trace 21 exhibits a periodic or gradual modulation, rather than a random and drastic jump. This regular impedance change is easier to predict and optimize through simulation, and can achieve good overall impedance matching over the entire phase shifter length, reducing multiple reflections caused by impedance discontinuities and ensuring signal integrity.

[0166] Optionally, at least some of the transmission sub-units 60 have the same impedance.

[0167] When the impedances of different transmission subunits 60 are mismatched, some radio frequency signals will be reflected, resulting in increased loss and affecting the transmission quality of radio frequency signals.

[0168] In this embodiment, by setting at least some of the transmission sub-units 60 to have the same impedance, good impedance matching can be maintained in different parts of the phase shifter trace 101, reducing the reflection and loss of radio frequency signals and improving the transmission efficiency of radio frequency signals.

[0169] Understandably, in order to achieve a uniform impedance distribution on the phase shifter trace 101, all transmission sub-units 60 can be configured to have the same impedance.

[0170] Optionally, in the transmission sub-unit 60, the stub trace 22 and the overlapping ground electrode layer 103 form an equivalent capacitance, and the sub-cutout region 301 forms an equivalent inductance. The ratio of the equivalent inductance to the equivalent capacitance is the same for different transmission sub-units 60.

[0171] Specifically, as mentioned above, the sub-cutout area 301 and the overlapping portion of the main trace 21 constitute a defective ground structure (DGS), which can be equivalent to an inductor element, i.e., an equivalent inductance 30L. Meanwhile, the stub trace 22 and the overlapping ground electrode layer 103 can be equivalent to a parallel-plate capacitor, i.e., an equivalent capacitance 30C.

[0172] Furthermore, impedance Satisfy the formula ;

[0173] in, Distributed inductance refers to the inductance value per unit length.

[0174] Distributed capacitance refers to the capacitance per unit length.

[0175] In this embodiment, by setting the ratio between the inductance value of the equivalent inductor 30L and the capacitance value of the equivalent capacitor 30C in different transmission sub-units 60 to be equal, different transmission sub-units 60 have the same impedance, thereby maintaining good impedance matching in different parts of the phase shifter trace 101, reducing the reflection and loss of radio frequency signals, and improving the transmission efficiency of radio frequency signals.

[0176] It should be noted that the inductance value of the equivalent inductance 30L of the defect ground structure formed by the sub-cutout area 301 and the overlapping part of the main trace 21 depends on its geometric parameters, such as the size of the sub-cutout area 301 and the size of the main trace 21.

[0177] Among them, electromagnetic simulation tools can be used for modeling and simulation to calculate the equivalent inductance of the defective ground structure, 30L. The simulation tools can accurately calculate the inductive effect of the defective ground structure based on specific geometric parameters and material properties.

[0178] It is understood that those skilled in the art can design the dimensions of the sub-cutout area 301 and the main trace 21 to achieve the required equivalent inductance value 30L. For example, a larger sub-cutout area 301 and a smaller main trace 21 line width can increase the equivalent inductance value 30L. This embodiment of the invention does not specifically limit this.

[0179] Similarly, the capacitance value of the equivalent capacitance 30C formed by the branch trace 22 and the grounding electrode layer 103 opposite to it can also be modeled and simulated using electromagnetic simulation tools and calculated.

[0180] It is understood that those skilled in the art can design the dimensions of the stub trace 22 to achieve the required equivalent capacitance 30C. For example, increasing the overlap area between the stub trace 22 and the ground electrode layer 103 disposed opposite to it, and decreasing the spacing between the stub trace 22 and the ground electrode layer 103 disposed opposite to it, can increase the equivalent capacitance 30C. This embodiment of the present invention does not specifically limit this.

[0181] Optionally, at least some of the transmission sub-units 60 have the same equivalent inductance and at least some of the transmission sub-units 60 have the same equivalent capacitance.

[0182] Specifically, as mentioned earlier, impedance Satisfy the formula .

[0183] Therefore, in this embodiment, by setting the equivalent inductance 30L of at least some of the transmission sub-units 60 to have equal inductance values ​​and the equivalent capacitance 30C of at least some of the transmission sub-units 60 to have equal capacitance values, at least some of the transmission sub-units 60 are made to have the same impedance, thereby maintaining good impedance matching in different parts of the phase shifter trace 101, reducing the reflection and loss of radio frequency signals, and improving the transmission efficiency of radio frequency signals.

[0184] Furthermore, as mentioned above, the inductance value of the equivalent inductance 30L of the defective ground structure formed by the sub-cutout region 301 and the overlapping portion of the main trace 21 depends on its geometric parameters. Therefore, the inductance value of the equivalent inductance 30L of at least some of the transmission sub-units 60 can be made equal by setting the geometric parameters of the defective ground structure in at least some of the transmission sub-units 60 to be consistent.

[0185] For example, at least some of the transmission sub-units 60 have the same size for the sub-cutout regions 301 and the same size for the main traces 21, so as to achieve that the inductance values ​​of the equivalent inductance 30L of at least some of the transmission sub-units 60 are equal, but are not limited to this.

[0186] Similarly, the capacitance value of the equivalent capacitance 30C formed by the stub trace 22 and the ground electrode layer 103 disposed opposite to it also depends on its geometric parameters. Therefore, the inductance value of the equivalent inductance 30L in at least some of the transmission sub-units 60 can be made equal by setting the geometric parameters of the defective ground structure in at least some of the transmission sub-units 60 to be consistent.

[0187] For example, the overlap area of ​​the stub trace 22 and the ground electrode layer 103 disposed opposite to it in at least a portion of the transmission sub-unit 60 is the same, and the spacing between the stub trace 22 and the ground electrode layer 103 disposed opposite to it is the same, so as to achieve that the capacitance value of the equivalent capacitor 30C in at least a portion of the transmission sub-unit 60 is equal, but it is not limited to this.

[0188] It should be noted that the impedance in the embodiments of the present invention refers to the characteristic impedance, which is the impedance per unit length on the phase shifter trace 101 when the radio frequency signal is propagated on the phase shifter trace 101.

[0189] In this embodiment, the characteristic impedance can be set to 50 ohms. 50 ohms can achieve a good balance between the medium in air (such as free space) and typical printed circuit board (PCB) materials, providing sufficient bandwidth while maintaining low loss. However, it is not limited to this, and the embodiments of the present invention do not make specific limitations on it.

[0190] Furthermore, in the transmission sub-unit 60, the inductance value of the equivalent inductance 30L of the defect ground structure formed by the sub-cutout area 301 and the main trace 21 overlapping therewith, and the capacitance value of the equivalent capacitance 30C formed by the stub trace 22 and the ground electrode layer 103 disposed opposite therewith, can be set according to the characteristic impedance.

[0191] In the transmission subunit 60, the inductance value of the equivalent inductance 201L of the defect ground structure formed by the sub-cutout region 301 and the main trace 21 can be on the order of nH (for example, between a few nH and tens of nH), and the capacitance value of the equivalent capacitance 202C formed by the stub trace 22 and the ground electrode layer 103 disposed opposite to it can be on the order of pF (for example, between a few pF and tens of pF). This embodiment of the invention does not specifically limit this.

[0192] Furthermore, in the transmission sub-unit 60, the dimensions of the defect ground structure formed by the sub-cutout area 301 and the main trace 21 overlapping therewith, as well as the dimensions of the stub trace 22 and the ground electrode layer 103 disposed opposite thereto, can be set according to the requirements for the inductance value of the equivalent inductance 30L and the capacitance value of the equivalent capacitance 30C.

[0193] For example, in the transmission subunit 60, along the extension direction of the phase shifter trace 101 (i.e., the direction of radio frequency signal transmission on the phase shifter trace 101), the length of the main trace 21 in the transmission subunit 60 can be set to about 100 micrometers, and the length of the stub trace 22 can also be set to about 100 micrometers to achieve better antenna performance in high-frequency applications, but it is not limited to this.

[0194] Figure 20 This is a schematic diagram of another phase shifter provided in an embodiment of the present invention, as shown below. Figure 20 As shown, optionally, multiple phase shifting units 10 are arranged in an array along the first direction X and the second direction Y. Along the first direction X and / or the second direction Y, the transmission sub-units 60 that are close to each other in two adjacent phase shifting units 10 are staggered. The second direction Y is parallel to the extension direction of the stub trace 22.

[0195] Specifically, such as Figure 20 As shown, multiple phase-shifting units 10 are arranged on a plane along the first direction X and the second direction Y with a certain row spacing and column spacing to form a regular two-dimensional array.

[0196] In the phase shifting unit array 10, any two adjacent phase shifting units 10 each contain a transmission subunit 60. In this embodiment, the two transmission subunits 60 that are spatially closest to each other in adjacent phase shifting units 10 are not aligned in the first direction X and / or the second direction Y, but are staggered.

[0197] Specifically, such as Figure 20As shown, in two adjacent phase shifting units 10 in the row direction (such as the second direction Y), the two transmission sub-units 60 with the closest spatial positions are displaced in the column direction (such as the first direction X) so that the two transmission sub-units 60 are not located in the same row, and are thus staggered in the row direction.

[0198] In other embodiments, in two adjacent phase shifting units 10 in the column direction (such as the second direction X), the two transmission sub-units 60 with the closest spatial positions are displaced in the row direction (such as the second direction Y) so that the two transmission sub-units 60 are not located in the same column, thereby being staggered in the column direction.

[0199] If the two transmission sub-units 60 that are closest to each other in spatial position in adjacent phase shifting units 10 are completely aligned, in order to ensure that there is sufficient isolation distance between the transmission sub-units 60 in adjacent phase shifting units 10, the row spacing and column spacing of the entire phase shifting unit 10 array will be limited to the sum of the size of the phase shifting unit 10 itself and the safety spacing.

[0200] In this embodiment, by staggering the two transmission sub-units 60 that are closest to each other in spatial position in adjacent phase shifting units 10, the transmission sub-units 60 of adjacent phase shifting units 10 can avoid each other in space. Under the premise of maintaining the same isolation between phase shifting units 10, the row spacing and column spacing of the phase shifting unit 10 array can be significantly reduced, the integration of the phase shifter can be improved, and miniaturized design can be achieved.

[0201] Based on the same inventive concept, this invention also provides an antenna, which includes the phase shifter described in any embodiment of this invention. Therefore, the antenna provided by this invention has the technical effects of the technical solutions in any of the above embodiments. The explanations of the same or corresponding structures and terms as described in the above embodiments will not be repeated here.

[0202] Figure 21 This is a schematic diagram of an antenna structure provided in an embodiment of the present invention. Figure 22 This is a schematic diagram of a partial cross-sectional structure of an antenna provided in an embodiment of the present invention, as shown below. Figure 21 and Figure 22 As shown, optionally, the antenna also includes a feed network 70 and a radiating electrode 71, with the feed network 70 coupled to the phase shifter trace 101. Along a direction perpendicular to the plane of the ground electrode layer 103, the ground electrode layer 103 and the radiating electrode 71 at least partially overlap. The ground electrode layer 103 includes a first cutout 1031, and along a direction perpendicular to the plane of the ground electrode layer 103, the phase shifter trace 101 and the first cutout 1031 at least partially overlap, with the radiating electrode 71 covering the first cutout 1031.

[0203] Specifically, such as Figure 21 andFigure 22 As shown, the radiating electrode 71 can be located on the side of the ground electrode layer 103 away from the phase shifter trace 101. The ground electrode layer 103 is provided with a first cutout portion 1031. The vertical projection of the radiating electrode 71 on the plane of the ground electrode layer 103 covers the first cutout portion 1031. The radio frequency signal is transmitted between the phase shifter trace 101 and the ground electrode layer 103. The adjustable dielectric layer 102 between the phase shifter trace 101 and the ground electrode layer 103 phase-shifts the radio frequency signal to change the phase of the radio frequency signal. The phase-shifted radio frequency signal is coupled to the radiating electrode 71 at the first cutout portion 1031 of the ground electrode layer 103. The radiating electrode 71 radiates the signal outward.

[0204] The shape and size parameters of the first hollow part 1031 can be set according to the actual situation, and the embodiments of the present invention do not limit this.

[0205] It should be noted that the radiation electrode 71 can be set in correspondence with the phase shifting unit 10. For example, the radiation electrode 71 and the phase shifting unit 10 can be set in one-to-one correspondence, and the radiation electrodes 71 corresponding to different phase shifting units 10 can be insulated from each other.

[0206] In other embodiments, the radiation electrode 71 may also be located on the side of the phase shifter trace 101 away from the ground electrode layer 103, that is, the phase shifter is inverted. This embodiment of the present invention does not specifically limit this.

[0207] Continue to refer to Figure 21 and Figure 22 Optionally, the antenna in this embodiment of the invention further includes a feed network 70, which is used to transmit radio frequency signals to each phase shifting unit 10. The feed network 70 may be distributed in a tree-like manner and include multiple branches, with each branch providing a radio frequency signal to one phase shifting unit 10.

[0208] like Figure 21 and Figure 22 As shown, the feed network 70 can be disposed on the same layer as the radiating electrode 71, that is, the feed network 70 and the radiating electrode 71 are disposed on the same plane. In this case, the feed network 70 and the phase shifter trace 101 are located on different layers. A second cutout portion 1032 can be provided on the ground electrode layer 103. The vertical projection of the feed network 70 on the plane where the ground electrode layer 103 is located overlaps at least partially with the second cutout portion 1032, so that the radio frequency signal transmitted by the feed network 70 is coupled to the phase shifter trace 101 at the second cutout portion 1032 of the ground electrode layer 103. Then, by controlling the dielectric constant of the adjustable dielectric layer 102, the radio frequency signal on the phase shifter trace 101 can be phase-shifted.

[0209] It should be noted that, in this embodiment, by setting the feed network 70 and the radiating electrode 71 on the same layer, the feed network 70 and the phase shifter trace 101 can be set separately, which helps to prevent the voltage signal transmitted in the phase shifter trace 101 from interfering with each phase shifting unit 10 and improves the reliability of the antenna operation.

[0210] In other embodiments, the feed network 70 may also be disposed on the same layer as the phase shifter trace 101, that is, the feed network 70 and the phase shifter trace 101 are disposed on the same plane. In this case, the feed network 70 and the phase shifter trace 101 are coupled and connected. Compared with the RF signal transmitted by the feed network 70 being coupled to the phase shifter trace 101 through the adjustable dielectric layer 102, the feed network 70 can directly transmit the RF signal to the phase shifter trace 101, thereby reducing RF signal loss and improving antenna performance. This embodiment of the present invention does not make specific limitations in this regard.

[0211] Continue to refer to Figure 21 and Figure 22 Optionally, the antenna provided in this embodiment of the invention further includes a radio frequency (RF) signal interface 72 and a solder pad 73. One end of the RF signal interface 72 is connected to the feed network 70 and fixed by the solder pad 73, while the other end of the RF signal interface 72 is used to connect to external circuits such as high-frequency connectors. The RF signal interface 72 can be configured according to actual conditions. Figure 21 and Figure 22 The settings shown are only one optional configuration.

[0212] Continue to refer to Figure 21 and Figure 22 Optionally, the phase shifter also includes a frame 74, which surrounds the adjustable dielectric layer 102 and can be used to support the first substrate 11 and the second substrate 12, thereby providing a receiving space for the adjustable dielectric layer 102 and sealing the adjustable dielectric layer 102.

[0213] It should be understood that the various forms of processes shown above can be used, with steps reordered, added, or deleted. For example, the steps described in this invention can be executed in parallel, sequentially, or in different orders, as long as the desired result of the technical solution of this invention can be achieved, and this is not limited herein.

[0214] The specific embodiments described above do not constitute a limitation on the scope of protection of this invention. Those skilled in the art should understand that various modifications, combinations, sub-combinations, and substitutions can be made according to design requirements and other factors. Any modifications, equivalent substitutions, and improvements made within the spirit and principles of this invention should be included within the scope of protection of this invention.

Claims

1. A phase shifter, characterized in that, It includes at least one phase shifting unit, the phase shifting unit includes a phase shifter trace, an adjustable dielectric layer and a ground electrode layer, the phase shifter trace and the ground electrode layer are disposed opposite to each other, and the adjustable dielectric layer is located between the phase shifter trace and the ground electrode layer; The phase shifter trace includes a main trace and at least one branch trace that intersects and connects with the main trace. The ground electrode layer includes at least one patterned region. The patterned region includes at least two sub-cutout regions arranged along a first direction and a portion of the ground electrode layer between adjacent sub-cutout regions. The first direction is parallel to the extension direction of the main trace. The orthographic projection of the branch trace on the plane where the ground electrode layer is located lies between the orthographic projections of the two adjacent sub-cutout regions on the plane where the ground electrode layer is located, and overlaps with the ground electrode layer between the two adjacent sub-cutout regions.

2. The phase shifter according to claim 1, characterized in that, The two adjacent sub-cutout areas are connected, and the orthographic projection of the connected area on the plane where the ground electrode layer is located overlaps with the orthographic projection of the intersection area of ​​the main trace and the branch trace on the plane where the ground electrode layer is located; The grounding electrode layer between two adjacent sub-cutout areas includes two spacers located on both sides of the connecting area along a second direction, which is parallel to the extension direction of the branch trace.

3. The phase shifter according to claim 2, characterized in that, The two spacers are symmetrically arranged with respect to the connected region.

4. The phase shifter according to claim 1, characterized in that, The length of the sub-cutout area along the first direction is greater than or equal to the length along the second direction, which is parallel to the extension direction of the branch line.

5. The phase shifter according to claim 4, characterized in that, The two adjacent sub-cutout areas are connected, and the orthographic projection of the connected area on the plane where the ground electrode layer is located overlaps with the orthographic projection of the intersection area of ​​the main trace and the branch trace on the plane where the ground electrode layer is located; the ground electrode layer between the two adjacent sub-cutout areas includes two spacers, and the two spacers are located on both sides of the connected area along the second direction; The length of the spacer along the first direction is greater than or equal to the length along the second direction.

6. The phase shifter according to claim 1, characterized in that, The length of the sub-hollow area along the first direction is less than the length along the second direction, which is parallel to the extension direction of the branch line.

7. The phase shifter according to claim 1, characterized in that, The orthographic projections of two adjacent sub-cutout areas onto the plane of the grounding electrode layer are symmetrically arranged with respect to the central axis of the orthographic projection of the branch trace onto the plane of the grounding electrode layer.

8. The phase shifter according to claim 1, characterized in that, The branch routing is symmetrically arranged with respect to the central axis of the main routing.

9. The phase shifter according to claim 1, characterized in that, The same sub-cutout area is symmetrically arranged with respect to the central axis of the orthographic projection of the main trace onto the plane where the ground electrode layer is located.

10. The phase shifter according to claim 1, characterized in that, The length of the branch trace along the second direction is greater than the length of the sub-hollow area along the second direction, and the second direction is parallel to the extension direction of the branch trace.

11. The phase shifter according to claim 1, characterized in that, The branch trace includes a first portion and a second portion that are connected to each other. The orthographic projection of the first portion on the plane where the ground electrode layer is located is located between adjacent sub-cutout areas. The second portion is located on at least one side of the first portion along a second direction. The second direction is parallel to the extension direction of the branch trace. The length of the second portion along the first direction is greater than or equal to the length of the first portion along the first direction.

12. The phase shifter according to claim 11, characterized in that, The second portion of the branch wiring is located on one side of the first portion along the second direction.

13. The phase shifter according to claim 12, characterized in that, The second portion of the branch wiring is located on the same side of the first portion along the second direction.

14. The phase shifter according to claim 12, characterized in that, The second portion of the adjacent branch routing is located on a different side of the first portion along the second direction.

15. The phase shifter according to claim 11, characterized in that, The second portion of the branch wiring is located on both sides of the first portion along the second direction; The branch routing is in the shape of an "I".

16. The phase shifter according to claim 11, characterized in that, The second portion has a length of L1 in the first direction, and the total length of the grounding electrode layer between the two adjacent sub-cutout regions and the two sub-cutout regions in the first direction is L2, where L1 ≤ L2.

17. The phase shifter according to claim 1, characterized in that, The length of the branch trace along the second direction is less than or equal to the length of the sub-cutout area along the second direction, and the second direction is parallel to the extension direction of the branch trace.

18. The phase shifter according to claim 1, characterized in that, The number of sub-cutout areas in the patterned area is 2 or 3.

19. The phase shifter according to claim 1, characterized in that, The branch traces and their corresponding overlapping patterned regions constitute a transmission sub-unit. In the same phase-shifting unit, the transmission sub-units are arranged along the winding direction of the main trace.

20. The phase shifter according to claim 19, characterized in that, At least some of the transmission sub-units have the same impedance.

21. The phase shifter according to claim 20, characterized in that, In the transmission subunit, the branch traces and the overlapping ground electrode layer form an equivalent capacitance, and the sub-cutout area forms an equivalent inductance; The ratio of the equivalent inductance to the equivalent capacitance is the same for all of the different transmission sub-units.

22. The phase shifter according to claim 21, characterized in that, At least some of the transmission sub-units have the same equivalent inductance, and at least some of the transmission sub-units have the same equivalent capacitance.

23. The phase shifter according to claim 19, characterized in that, The multiple phase-shifting units are arranged in an array along the first direction and the second direction. Along the first direction and / or the second direction, the transmission sub-units that are close to each other in two adjacent phase-shifting units are staggered. The second direction is parallel to the extension direction of the stub trace.

24. An antenna, characterized in that, Includes the phase shifter according to any one of claims 1-23.

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