Data processing method, device and equipment

Abstract

The invention discloses a data processing method, device and equipment, and belongs to the technical field of communication, and the data processing method comprises the steps that first equipment carries out first processing on first data to obtain second data, the first data is data corresponding to a sensing signal, and the second data is data corresponding to the sensing signal; the first processing is used for aligning time delay spectrums of M symbols in the first data, the M symbols are M symbols occupied by the sensing signal, and M is an integer greater than 1; and the first device carries out second processing on the second data to obtain third data, and the second processing is used for carrying out phase compensation on time delay spectrums of at least part of symbols in the M symbols in the second data.

Description

Technical Field

[0001] This application belongs to the field of communication technology, and specifically relates to a data processing method, apparatus and device. Background Technology

[0002] In a sensing scenario, the transmitter and receiver of the sensing signal use their respective frequency sources to generate local oscillator signals and clock signals for transmission and reception. The clock signals between the transceivers may differ, leading to timing skew. This timing skew results in timing drift, specifically caused by the difference in clock periods between the receiver's clock and the transmitter's clock. The timing drift changes over time across each symbol. Furthermore, for some low-cost devices transmitting sensing signals, random phase shifts may occur due to factors such as uplink / downlink switching. Therefore, at least one of timing drift and random phase shifts may exist in a sensing scenario. Timing drift and random phase shifts introduce additional, unknown phase deviations between symbols of the sensing signal, and timing drift causes delay spectrum shifts between symbols. Thus, sensing scenarios suffer from both phase deviation and delay spectrum shift issues. Summary of the Invention

[0003] This application provides a data processing method, apparatus, and device that can solve the problems of phase deviation and time delay spectrum shift in a sensing scenario.

[0004] Firstly, a data processing method is provided, including:

[0005] The first device performs a first process on the first data to obtain the second data. The first data is the data corresponding to the sensing signal. The first process is used to align the time delay spectrum of M symbols in the first data. The M symbols are the M symbols occupied by the sensing signal, and M is an integer greater than 1.

[0006] The first device performs a second processing on the second data to obtain third data. The second processing is used to perform phase compensation on the time delay spectrum of at least some of the M symbols in the second data.

[0007] Secondly, a data processing apparatus is provided, comprising:

[0008] The processing module is used to perform a first processing on the first data to obtain the second data. The first data is the data corresponding to the sensing signal. The first processing is used to align the time delay spectrum of M symbols in the first data. The M symbols are the M symbols occupied by the sensing signal, and M is an integer greater than 1.

[0009] The processing module is further configured to perform a second processing on the second data to obtain third data, wherein the second processing is used to perform phase compensation on the time delay spectrum of at least some of the M symbols in the second data.

[0010] Thirdly, a data processing apparatus is provided, the apparatus being configured to perform the steps of the data processing method provided in the embodiments of this application.

[0011] Fourthly, an apparatus is provided, comprising a processor and a memory, the memory storing a program or instructions executable on the processor, the program or instructions, when executed by the processor, implementing the steps of the data processing method provided in the embodiments of this application.

[0012] Fifthly, a device is provided, including a processor and a communication interface, wherein the processor is configured to perform a first processing on first data to obtain second data, the first data being data corresponding to a sensing signal, the first processing being configured to align the time delay spectra of M symbols in the first data, the M symbols being the M symbols occupied by the sensing signal, M being an integer greater than 1; and to perform a second processing on the second data to obtain third data, the second processing being configured to perform phase compensation on the time delay spectra of at least some of the M symbols in the second data.

[0013] In a sixth aspect, a readable storage medium is provided, on which a program or instructions are stored, which, when executed by a processor, implement the steps of the data processing method provided in the embodiments of this application.

[0014] In a seventh aspect, a chip is provided, the chip including a processor and a communication interface, the communication interface being coupled to the processor, the processor being used to run programs or instructions to implement the data processing method provided in the embodiments of this application.

[0015] Eighthly, a computer program / program product is provided, which is stored in a storage medium and is executed by at least one processor to implement the steps of the data processing method provided in the embodiments of this application.

[0016] In this embodiment, a first device performs a first process on first data to obtain second data. The first data is data corresponding to a sensing signal. The first process aligns the time delay spectra of M symbols in the first data, where M symbols are the M symbols occupied by the sensing signal, and M is an integer greater than 1. The first device then performs a second process on the second data to obtain third data. The second process performs phase compensation on the time delay spectra of at least some of the M symbols in the second data. Thus, the first process aligns the time delay spectra of the first data across the M symbols, solving the problem of time delay spectrum shift. The second process performs phase compensation on the time delay spectra of at least some of the M symbols in the second data, solving the problem of phase deviation. Furthermore, by resolving the problems of phase deviation and time delay spectrum shift, the sensing results obtained from subsequent processing become more accurate, thereby improving sensing performance. Attached Figure Description

[0017] Figure 1 This is a schematic diagram of a system provided in an embodiment of this application;

[0018] Figure 2 This is a schematic diagram of a sensing and measurement scenario provided in an embodiment of this application;

[0019] Figure 3 This is a schematic diagram of a sampling clock deviation provided in an embodiment of this application;

[0020] Figure 4 This is a schematic diagram of a timing drift value provided in an embodiment of this application;

[0021] Figure 5 This is a schematic diagram of a time delay-Doppler spectrum under the influence of timing drift, provided in an embodiment of this application;

[0022] Figure 6 This is a flowchart of a data processing method provided in an embodiment of this application;

[0023] Figure 7 This is a schematic diagram of a time delay spectrum provided in an embodiment of this application;

[0024] Figure 8 This is a schematic diagram of another time delay spectrum provided in an embodiment of this application;

[0025] Figure 9 This is a schematic diagram of another time delay spectrum provided in an embodiment of this application;

[0026] Figure 10 This is a schematic diagram illustrating a phase compensation effect provided in an embodiment of this application;

[0027] Figure 11This is a schematic diagram of a time delay spectrum shift provided in an embodiment of this application;

[0028] Figure 12 This is a structural diagram of a data processing apparatus provided in an embodiment of this application;

[0029] Figure 13 This is a structural diagram of a communication device provided in an embodiment of this application;

[0030] Figure 14 This is a structural diagram of a device provided in an embodiment of this application. Detailed Implementation

[0031] The technical solutions of the embodiments of this application will be clearly described below with reference to the accompanying drawings. Obviously, the described embodiments are only some, not all, of the embodiments of this application. All other embodiments obtained by those skilled in the art based on the embodiments of this application are within the scope of protection of this application.

[0032] The terms "first," "second," etc., used in this application are used to distinguish similar objects and not to describe a specific order or sequence. It should be understood that such terms can be used interchangeably where appropriate so that embodiments of this application can be implemented in orders other than those illustrated or described herein, and the objects distinguished by "first" and "second" are generally of the same class, not limited in number; for example, the first object can be one or more. Furthermore, "or" in this application indicates at least one of the connected objects. For example, the scope of protection for "A or B" covers at least three scenarios: Scenario 1: including A but not B; Scenario 2: including B but not A; Scenario 3: including both A and B. In addition, the terms "A and / or B," "at least one of A and B," and "at least one of A or B" also cover at least the above three scenarios. The character " / " generally indicates that the preceding and following objects are in an "or" relationship.

[0033] The term "instruction" in this application can be either a direct instruction (or explicit instruction) or an indirect instruction (or implicit instruction). A direct instruction can be understood as one in which the sender explicitly informs the receiver of specific information, the operation to be performed, or the requested result, etc., in the instruction sent. An indirect instruction can be understood as one in which the receiver determines the corresponding information based on the instruction sent by the sender, or makes a judgment and determines the operation to be performed or the requested result, etc., based on the judgment result.

[0034] It is worth noting that the technology described in the embodiments of this application is not limited to Long Term Evolution (LTE) / LTE-Advanced (LTE-A) systems, but can also be used in other wireless communication systems, such as Code Division Multiple Access (CDMA), Time Division Multiple Access (TDMA), Frequency Division Multiple Access (FDMA), Orthogonal Frequency Division Multiple Access (OFDMA), Single-carrier Frequency-Division Multiple Access (SC-FDMA), or other systems.

[0035] The terms "system" and "network" used in the embodiments of this application are often used interchangeably, and the described technologies can be used with respect to the systems and radio technologies mentioned above, as well as other systems and radio technologies. The following description describes a New Radio (NR) system for illustrative purposes, and the term NR is used in most of the following description; however, these technologies can also be applied to systems other than NR systems, such as 6th generation (6G) systems. th Generation 6G communication system.

[0036] Figure 1 This diagram illustrates a block diagram of a wireless communication system applicable to embodiments of this application. The wireless communication system includes a terminal 11 and a network-side device 12.

[0037] Terminal 11 can be a mobile phone, tablet computer, laptop computer, notebook computer, personal digital assistant (PDA), handheld computer, netbook, ultra-mobile personal computer (UMPC), mobile internet device (MID), augmented reality (AR), virtual reality (VR) device, robot, wearable device, flight vehicle, vehicle user equipment (VUE), shipboard equipment, pedestrian user equipment (PUE), smart home (home devices with wireless communication capabilities, such as refrigerators, televisions, washing machines, or furniture), game console, personal computer (PC), ATM, or self-service machine, etc. Wearable devices include: smartwatches, smart bracelets, smart earphones, smart glasses, smart jewelry (smart bracelets, smart chains, smart rings, smart necklaces, smart anklets, smart anklets, etc.), smart wristbands, smart clothing, etc. Among these, in-vehicle devices can also be referred to as in-vehicle terminals, in-vehicle controllers, in-vehicle modules, in-vehicle components, in-vehicle chips, or in-vehicle units, etc. It should be noted that the specific type of terminal 11 is not limited in the embodiments of this application.

[0038] Network-side equipment 12 may include access network equipment or core network equipment. Access network equipment may also be referred to as Radio Access Network (RAN) equipment, radio access network function, radio access network unit, or satellite. Access network equipment may include base stations, Wireless Local Area Network (WLAN) access points (AS), or Wireless Fidelity (WiFi) nodes, etc. In this context, a base station may be referred to as a Node B (NB), Evolved Node B (eNB), Next Generation Node B (gNB), New Radio Node B (NR Node B), Access Point, Relay Base Station (RBS), Serving Base Station (SBS), Base Transceiver Station (BTS), Radio Base Station, Radio Transceiver, Basic Service Set (BSS), Extended Service Set (ESS), Home Node B (HNB), Home Evolved Node B, Transmit / Receive Point (TRP), or any other suitable term in the relevant field, as long as the same technical effect is achieved. The base station is not limited to any specific technical terminology. It should be noted that in this application embodiment, only a base station in an NR system is used as an example for introduction, and the specific type of base station is not limited.

[0039] Core network equipment, also known as core network nodes, core network functions, or core network elements, includes, but is not limited to, at least one of the following: Mobility Management Entity (MME), Access and Mobility Management Function (AMF), Session Management Function (SMF), User Plane Function (UPF), Policy Control Function (PCF), Policy and Charging Rules Function (PCRF), Edge Application Server Discovery Function (EASDF), Unified Data Management (UDM), Unified Data Repository (UDR), Home Subscriber Server (HSS), Centralized network configuration (CNC), Network Repository Function (NRF), Network Exposure Function (NEF), Local NEF (or L-NEF), and Binding Support Function. Support Functions (BSF), Application Functions (AF), Location Management Functions (LMF), Gateway Mobile Location Centres (GMLC), and Network Data Analytics Functions (NWDAF), etc. It should be noted that this application embodiment only uses core network equipment in the NR system as an example and does not limit the specific type of core network equipment. If the name of the core network equipment mentioned in this application embodiment changes in subsequent protocol versions (e.g., 6G), it will still be within the scope of protection of this application.

[0040] Optionally, the core network equipment can be implemented by one or more functional modules in a single device, or by multiple devices working together; this application does not specifically limit this. It is understood that the aforementioned functional modules can be network elements in hardware devices, software functional modules running on dedicated hardware, or virtualized functional modules instantiated on a platform (e.g., a cloud platform).

[0041] In some embodiments, future Beyond 5G (B5G) and 6G wireless communication systems are expected to provide a variety of high-precision sensing services, such as indoor positioning for robot navigation, Wi-Fi sensing for smart homes, and radar sensing for autonomous vehicles. Sensing and communication systems are typically designed separately and occupy different frequency bands. Integrated Sensing and Communication (ISAC) enables sensing and communication systems to share the same frequency band and hardware, improving frequency efficiency and reducing hardware costs. ISAC will become a key technology for future wireless communication systems to support many important application scenarios. Typical applications of ISAC include: navigation and obstacle avoidance for autonomous vehicles, Wi-Fi-based indoor positioning and activity recognition, communication and sensing for unmanned aerial vehicles, extended reality (XR), and radar and communication integration. Each application has different requirements, limitations, and regulatory issues. ISAC has already attracted significant research interest and attention from academia and industry.

[0042] JSAC achieves integrated, low-cost implementation of both communication and sensing functions through shared hardware and software-defined features. Its main characteristics include: a unified and simplified architecture; reconfigurable and scalable functionality; and improved efficiency and reduced costs. The advantages of integrated communication and sensing are threefold: reduced equipment costs and smaller size; improved spectrum utilization; and enhanced system performance.

[0043] Currently, the typical scenarios of integrated communication and sensing that can be realized by upgrading the technology based on the 5G communication system architecture are shown in Table 1 below.

[0044] Table 1:

[0045]

[0046] In some embodiments, depending on the different sensing signal transmitting and receiving nodes, the methods may include, but are not limited to, those mentioned above. Figure 2 The six sensing links shown are... It should be noted that... Figure 2Each sensing link in the example is illustrated with one sending node and one receiving node. In a real system, different sensing links can be selected according to different sensing requirements. Each sensing link can have one or more sending and receiving nodes, and a real sensing system can include multiple different sensing links. Figure 2 The perception targets in this example are people and vehicles, and it is assumed that neither people nor vehicles carry or have signal receiving / transmitting equipment installed. In reality, the perception targets will be much richer.

[0047] Sensing Link 1: Base station self-transmitting and self-receiving sensing. In this method, the base station sends sensing signals and obtains the sensing results by receiving the echoes of these signals;

[0048] Sensing Link 2: Inter-base station air interface sensing. In this mode, base station 2 receives sensing signals sent by base station 1 and obtains the sensing results.

[0049] Sensing Link 3: Uplink air interface sensing. In this mode, the base station receives sensing signals sent by the terminal and obtains the sensing results.

[0050] Sensing Link 4: Downlink Air Interface Sensing. In this mode, the terminal receives sensing signals sent by the base station and obtains the sensing results.

[0051] Sensing Link 5: Terminal Self-Sending and Receiving Sensing. In this mode, the terminal sends a sensing signal and obtains the sensing result by receiving the echo of the sensing signal.

[0052] Sensing Link 6: Sidelink sensing between terminals. For example, terminal 2 receives a sensing signal sent by terminal 1 and obtains a sensing result, or terminal 1 receives a sensing signal sent by terminal 2 and obtains a sensing result.

[0053] It should be noted that, Figure 2 Each sensing method is illustrated with a sensing signal transmitter and a sensing signal receiver as an example. In actual systems, one or more different sensing methods can be selected according to different sensing use cases and sensing requirements, and each sensing method can have one or more transmitters and receivers. Figure 2 The perception targets in this example are people and vehicles, and it is assumed that neither people nor vehicles carry or have signal receiving / transmitting equipment installed. In reality, the perception targets will be much richer.

[0054] exist Figure 2Of the six basic sensing methods shown, in four methods—inter-base station air interface sensing, uplink air interface sensing, downlink air interface sensing, and inter-terminal sidelink sensing—the transmitter and receiver of the sensing signal belong to different devices; that is, these four sensing methods are dual-site sensing. However, in two sensing methods—base station self-transmission and self-reception sensing and terminal self-transmission and self-reception sensing—the transmitter and receiver of the sensing signal belong to the same device; that is, these two sensing methods are single-site sensing.

[0055] Dual-station sensing does not require the equipment to have full-duplex capability, and its signal propagation characteristics are essentially the same as those in existing communication systems. Therefore, dual-station sensing can fully utilize the hardware and signal design of existing communication systems, thus enabling truly integrated communication and sensing design at a lower cost. Furthermore, dual-station sensing, especially uplink or downlink air interface sensing, allows for flexible selection of the terminal equipment responsible for transmitting or receiving sensing signals. If a terminal equipment closer to the sensing target is selected, the signal propagation distance from the target to the terminal is shorter, resulting in lower signal propagation path loss and ultimately a gain in sensing signal power. Based on these advantages, dual-station sensing has remained a hot topic in integrated sensing research.

[0056] However, a significant challenge in bi-station sensing is the time-frequency asynchrony between the transmitter and receiver of the sensing signal. The transmitter and receiver each use their respective frequency sources to generate local oscillator and clock signals for transmitting and receiving the sensing signal. Differences in the local oscillator frequencies between the transceivers cause carrier frequency deviations, while differences in the clock signals cause timing deviations. The carrier frequency deviation results in an overall shift in the Doppler spectrum of the sensing signal, with the shift value being the carrier frequency deviation itself. The impact of timing deviations is more complex. For example... Figure 3 As shown, the timing deviation includes two parts: the timing start point deviation (τ in the figure) strat The timing drift (shown in the figure) and timing offset (Δτ1, Δτ2, Δτ3, etc.) are also present. Timing start point deviation is mainly caused by the overall deviation between the receiver clock and the transmitter clock of the sensed signal, resulting in an overall shift in the time delay spectrum. Timing drift, on the other hand, is caused by the difference in clock periods between the receiver clock and the transmitter clock of the sensed signal; the timing drift changes at each symbol as time progresses. Furthermore, timing drift can also jump when timing adjustments occur in the communication system.

[0057] Figure 4This diagram illustrates timing drift in a real-world measurement. In the time domain, there is a sensing signal with one symbol every 2 ms, totaling 100 symbols over a time span of 200 ms. The red arrows in the diagram indicate timing adjustments. According to the rules of the NR system, timing adjustments typically involve a jump in the time length corresponding to a time domain sampling point. Between any two timing adjustments, continuous timing drift changes occur.

[0058] Timing drift causes shifts and phase deviations in the time delay spectra of various symbols. Taking the localization application of passive sensing targets as an example, the shifts and phase deviations in the time delay spectrum will cause dispersion of the time delay-Doppler spectrum. Figure 4 The timing drift shown causes the time delay spectrum and time delay-Doppler spectrum as follows: Figure 5 As shown. Figure 5 In (a), the horizontal axis represents the symbol index and the vertical axis represents the subcarrier index. Figure 5 As shown in (a), the time delay spectra of each symbol are shifted. When the shift is less than an integer number of time delay units, a fence loss occurs, causing the sensed signal power to fall into two adjacent time delay units. Combined with the phase difference caused by timing drift, the final time delay-Doppler spectrum is as follows: Figure 5 As shown in (b) of the figure. The circled area in the figure indicates the position of the perceived target in the time-delay-Doppler spectrum. The time-delay-Doppler spectrum is severely diffused, making it impossible to detect the perceived target correctly.

[0059] The following description, in conjunction with the accompanying drawings, details a data processing method, apparatus, and device provided in this application through some embodiments and application scenarios.

[0060] Please see Figure 6 , Figure 6 This is a flowchart of a data processing method provided in an embodiment of this application, such as... Figure 6 As shown, it includes the following steps:

[0061] Step 601: The first device performs a first process on the first data to obtain the second data. The first data is the data corresponding to the sensing signal. The first process is used to align the time delay spectrum of M symbols in the first data. The M symbols are the M symbols occupied by the sensing signal, and M is an integer greater than 1.

[0062] The first device mentioned above can be a terminal or a network-side device.

[0063] The aforementioned sensing signal can be a sensing signal received by the first device from the second device.

[0064] The first data mentioned above is the data corresponding to the sensing signal. It can be obtained by the first device after receiving the sensing signal and performing steps such as down-conversion, filtering, analog-to-digital (AD) sampling, fast Fourier transform (FFT) operation, and channel estimation.

[0065] The above M symbols can be M OFDM symbols, and the symbols in the embodiments of this application can all refer to OFDM symbols.

[0066] The first process described above, which aligns the time delay spectra of the M symbols in the first data, can be understood as aligning the time delay spectra of each symbol.

[0067] The aforementioned first data includes M symbols, or it can be said that the aforementioned first data includes data corresponding to M symbols. The time delay spectrum of the M symbols in the aforementioned first data can be understood as the time delay spectrum of these M symbols or the time delay spectrum of the data corresponding to these M symbols.

[0068] In this embodiment of the application, the delay spectrum shift between symbols is eliminated by the first process, and the delay spectrum alignment is achieved to solve the problem of delay spectrum shift.

[0069] The first process described above can also be called time delay spectrum alignment operation or time delay spectrum alignment processing.

[0070] Step 602: The first device performs a second processing on the second data to obtain third data. The second processing is used to perform phase compensation on the time delay spectrum of at least some of the M symbols in the second data.

[0071] The second processing described above, used to perform phase compensation on the time delay spectrum of at least some of the M symbols in the second data, can be to perform phase compensation on the time delay spectrum of other symbols based on one of the symbols, or it can be to perform phase compensation on the time delay spectrum of all symbols.

[0072] The aforementioned second data includes M symbols, or the aforementioned second data includes data corresponding to M symbols. The time delay spectrum of at least some of the M symbols in the aforementioned second data can be understood as the time delay spectrum of at least some of the M symbols or the time delay spectrum of the data corresponding to at least some of the M symbols.

[0073] The aforementioned third data is used to obtain the perception result. For example, the first device obtains the perception result based on the aforementioned third data, or the first device sends the aforementioned third data to other devices, and the other devices obtain the perception result based on the aforementioned third data. In this embodiment of the application, the method of obtaining the perception result based on the aforementioned third data is not limited.

[0074] In this embodiment, the first processing aligns the time delay spectra of the first data across M symbols to resolve the time delay spectrum shifting problem. The second processing performs phase compensation on the time delay spectra of at least a portion of the M symbols in the second data to resolve the phase deviation problem. Furthermore, by addressing both phase deviation and time delay spectrum shifting, the resulting perception is more accurate, thus improving perception performance.

[0075] As an optional implementation, the first data is a channel matrix in the time-frequency domain, and the dimension of the first data is N×M.

[0076] The dimension of the first data mentioned above is N×M, which can be understood as the first data including M symbols, each OFDM symbol having N subcarriers, forming an N-row, M-column time-frequency domain channel matrix.

[0077] As an optional implementation, the first process includes:

[0078] Perform an inverse discrete Fourier transform (IDFT) on the first data at point P to obtain the time delay spectrum of the M symbols in the first data, where P is an integer greater than N and N is the number of subcarriers occupied by the sensing signal.

[0079] The time delay spectra of the M symbols in the first data are aligned.

[0080] The value of P mentioned above can be configured by the network-side device or agreed upon by the protocol.

[0081] The aforementioned P-point IDFT can be implemented using either oversampling IDFT or zero-padding IDFT. When the number of IDFT points is the same, oversampling IDFT and zero-padding IDFT are equivalent. Compared to the conventional IDFT, oversampling IDFT or zero-padding IDFT achieves better apparent resolution performance, with the apparent resolution of the time delay spectrum becoming N / P times that of the conventional IDFT.

[0082] In this embodiment of the application, IDFT can be implemented by inverse fast Fourier transform (IFFT).

[0083] The time delay spectrum of the M symbols obtained in the first data can be called the first intermediate result, specifically the time delay spectrum in the time-delay domain, with a dimension of P×M. That is, the first intermediate result includes M symbols, each with a time delay spectrum of P points. If oversampling IDFT (or zero-padding IDFT) is used to obtain the time delay spectrum, the resulting time delay spectrum is as follows: Figure 7 As shown, Figure 7 The horizontal axis represents the symbol index, and the vertical axis represents the apparent time delay resolution unit index. Figure 7 The number of symbols shown is M = 100, and the number of IDFT points is P = 8768; for ease of observation, Figure 7 The vertical axis only shows the range of 1 to 3200.

[0084] The above-mentioned alignment processing of the time delay spectrum of the M symbols in the first data can be performed by extracting the shift value between the time delay spectra of each symbol, and then aligning the time delay spectrum of the first data in the M symbols based on the shift value.

[0085] In the above embodiment, the first signal is subjected to P-point IDFT to obtain the time delay spectrum of the first data over M symbols. Then, the time delay spectrum of the first data over M symbols is aligned. This can eliminate the time delay spectrum shift between symbols and achieve time delay spectrum alignment.

[0086] It should be noted that, in the embodiments of this application, it is not limited to obtaining the time delay spectrum of the first data over M symbols by performing an IDFT on the first data at a P-point. For example, in some implementations, the time delay spectrum of the first data over M symbols can also be obtained through operations other than IDFT, and this is not limited.

[0087] Optionally, the alignment process for the time delay spectra of the M symbols in the first data includes:

[0088] Obtain the shift information between the time delay spectra of the M symbols in the first data;

[0089] The time delay spectrum of at least some of the M symbols in the first data is reverse cyclically shifted according to the shift information, and the reverse cyclic shift is used to align the time delay spectrum of the M symbols in the first data.

[0090] The shift information mentioned above can be a shift value.

[0091] The "reverse" in the above reverse circular shift refers to the polarity of the shift between each sign. For example, if δ kIf the value is a positive integer, it means that the time delay spectrum of the k-th symbol has been shifted relative to the reference symbol (such as the time delay spectrum of the j-th symbol) along the direction in which the time delay resolution cell index increases. Therefore, the aforementioned reverse cyclic shift involves performing a δ shift on the time delay spectrum of the k-th symbol along the direction in which the cell index decreases. k The shift of each unit, δ k This represents the shift value between the time delay spectra of two symbols; conversely, if δ k If the value is a negative integer, it means that the time delay spectrum of the k-th symbol has been shifted relative to the reference symbol (the time delay spectrum of the j-th OFDM symbol) along the direction where the cell index decreases. Therefore, the reverse circular shift involves shifting the time delay spectrum of the k-th symbol along the direction where the apparent cell index increases by |δ... k | Shift of each unit.

[0092] In this embodiment, the time delay spectrum of the first data over M symbols can be accurately aligned using the aforementioned reverse cyclic shift. For example: Figure 7 Taking the time delay spectrum shown as an example, the aligned data can be obtained as follows: Figure 8 As shown, Figure 8 The meaning of the coordinate system and Figure 7 The same as in [the previous sentence].

[0093] In some implementations, obtaining the shift information between the time delay spectra of the M symbols in the first data includes one of the following:

[0094] The shift information between the time delay spectra of the M symbols in the first data is obtained by means of a reference path.

[0095] The shift information between the delay spectra of the M symbols in the first data is obtained by using a group delay method.

[0096] Specifically, obtaining the shift information between the time delay spectra of the M symbols in the first data through the reference path method can be based on determining the shift information between the time delay spectra of the M symbols in the first data according to the time delay spectra of the reference path in the first data.

[0097] In some implementations, obtaining the shift information between the time delay spectra of the M symbols in the first data via a reference path method includes:

[0098] Obtain the cell index of the reference path in the time delay spectrum of the M symbols in the first data, and calculate the shift information based on the cell index. The shift information includes the difference between the cell indices corresponding to the M symbols, or the shift information includes the difference between the cell index corresponding to the M-1 symbols and the cell index corresponding to the first symbol.

[0099] In some implementations, the first symbol can be a reference symbol determined from M symbols. Specifically, it can be a network-side device configuration or protocol agreement of the first device determiner. This allows for the calculation of the shift value between the delay spectrum of the other M-1 symbols and the delay spectrum of this symbol.

[0100] The aforementioned reference diameter can be the diameter with the highest power.

[0101] The cell index of the reference path on the time delay spectrum can be the index of the time delay resolution cell or the apparent time delay resolution cell where the reference path is located on the time delay spectrum.

[0102] In this embodiment, the cells in the time delay spectrum can refer to either time delay resolution cells or apparent time delay resolution cells in the time delay spectrum. Specifically, an apparent time delay resolution cell refers to a cell in the time delay spectrum obtained by an IDFT operation with P > N points.

[0103] The difference between the cell indices corresponding to the above M symbols can represent the difference between the corresponding cell indices of any two symbols. For example, the cell indices of the reference paths on the M symbols in the time delay spectrum are denoted as {d1, d2, ..., d...}. M}, then the shift value between the time delay spectra of the j-th symbol and the k-th symbol is δ. k,j =d k -d j , where the j-th symbol and the k-th symbol can represent any two symbols.

[0104] The difference between the cell index corresponding to the M-1 symbols and the cell index corresponding to the first symbol can be understood as follows: The first symbol can be determined from the M symbols as a reference, and the shift values ​​of the time delay spectra of the other M-1 symbols and the time delay spectrum of the first symbol can be calculated. For example, a value of j can be fixed, and then the values ​​of k can be iterated through to calculate δ using the above method. k,j At this time, δ k,j The 'j' in the equation can be omitted, becoming 'δ'. k Obviously, there is δ k＝j =0.

[0105] In the above embodiments, the shift information between the time delay spectra of the M symbols in the first data can be obtained through the reference path. Since only the relevant information of the reference path needs to be calculated, the computational cost can be saved.

[0106] The aforementioned method of obtaining the shift information between the time delay spectra of the M symbols in the first data through group delay can be achieved by extracting the shift values ​​between the time delay spectra through cross-correlation operations, thereby obtaining the shift information between the time delay spectra of the M symbols in the first data.

[0107] In some implementations, obtaining the shift information between the delay spectra of the M symbols in the first data via group delay includes:

[0108] Based on the time delay spectra of the M symbols in the first data, the correlation spectrum between the second symbol and the first symbol is calculated, and the shift information includes the cell index corresponding to the maximum amplitude value in the correlation spectrum between the second symbol and the first symbol; or

[0109] Based on the time delay spectrum of the M symbols in the first data, the correlation spectrum of M-1 symbols with the first symbol is calculated respectively, and the shift information includes the cell index corresponding to the maximum amplitude value in the correlation spectrum of the M-1 symbols with the first symbol respectively;

[0110] Wherein, the first symbol is one of the M symbols, the M-1 symbols are the M-1 symbols other than the first symbol among the M symbols, and the second symbol is one of the M symbols other than the first symbol.

[0111] The second symbol mentioned above can be any symbol among the M symbols except for the first symbol, that is, the first symbol and the second symbol are two different symbols, such as the j-th symbol and the k-th symbol. In some embodiments, the first symbol can represent any symbol among the M symbols, thus enabling the calculation of the correlation spectrum of any two symbols.

[0112] The above calculation of the correlation spectrum between the M-1 symbols and the first symbol can be based on the first symbol, and the correlation spectrum between the other M-1 symbols and the reference symbol can be calculated.

[0113] In some implementations, the aforementioned correlation spectrum may include:

[0114] For r j and r k The first correlation spectrum obtained by performing cyclic cross-correlation, or the correlation spectrum obtained by |r j |and|r k The second correlation spectrum obtained by performing cyclic cross-correlation operation, wherein the r j and r k Let each of the two symbols in the M symbols of the first data represent the time delay spectrum, |r j |and|r k | The amplitude values ​​of the time delay spectrum of the two symbols respectively.

[0115] The above r j and r kThe time delay spectrum of the first data in the M symbols can represent the time delay spectrum of the j-th symbol and the k-th symbol, that is, the first correlation spectrum or the second correlation spectrum of the j-th symbol and the k-th symbol is calculated.

[0116] In the above embodiments, the shift information between the time delay spectra of the M symbols in the first data can be calculated using the correlation spectrum, which can improve the accuracy of the shift information.

[0117] As an optional implementation, the second data is the data obtained from the alignment process; or

[0118] The first process further includes:

[0119] The aligned data is downsampled by a factor of P / N along the time delay dimension, and the second data is the data obtained after the downsampling.

[0120] In this case, the second data obtained by the alignment process can be directly processed, which can reduce some of the computational steps in the second processing in some embodiments.

[0121] The above-mentioned downsampling of the aligned data along the time delay dimension by a factor of P / N enables the second data obtained by downsampling to undergo a second data processing, which can save the amount of data in the second processing.

[0122] Among them, corresponding to Figure 7 The time delay spectrum, after downsampling, yields the second data as follows: Figure 9 As shown, Figure 9 The horizontal axis represents the symbol index, and the vertical axis represents the time delay unit index of the downsampled time delay spectrum.

[0123] As an optional implementation, P is equal to α × N, where α is an integer obtained based on a first table, the first table including at least one index and at least one value of α;

[0124] Alternatively, P can be an integer obtained based on a second table, which includes at least one index and at least one value of P.

[0125] When P equals α × N, IDFT can be performed according to a specified multiple, that is, according to a certain multiple α, combined with the number of subcarriers N, the number of IDFT points in the first process is P = αN. When using this method, the above-mentioned first table (which can be called the first mapping table) is preset, which contains at least one available α value and its corresponding index. For example, the first table is shown in Table 2 below.

[0126] Table 2:

[0127] index α value 0 2 1 4 2 8 3 16 4 32 5 64 … …

[0128] In the above example, P equals α × N, and the resulting improvement in apparent resolution performance is an integer multiple. For instance, if the latency resolution using a conventional IDFT is Δτ, then the apparent resolution after using an oversampled IDFT (or zero-padded IDFT) is Δτ / α. Furthermore, after the alignment process, the data obtained from the alignment process can be downsampled, thereby reducing the amount of data processed subsequently.

[0129] In some implementations, the first table may include one or more tables, and P is determined based on one of the tables.

[0130] When P is an integer obtained from the second table, a specified number of IDFT points can be obtained, that is, P can be obtained directly according to the specified number of IDFT points. In this case, a second table (also called a second mapping table) is pre-defined, which contains at least one available P value and its corresponding index. For example, the second table is shown in Table 3 below.

[0131] Table 3:

[0132] index p-value 0 128 1 256 2 512 3 1024 4 2048 5 4096 6 8192 … …

[0133] When P is an integer obtained from the second table, it is possible to determine the IDFT points such that the final IDFT points are powers of 2 or 4, thereby accelerating the computation.

[0134] As an optional implementation, the second process includes:

[0135] Obtain the phase difference between the time delay spectra of the M symbols in the second data;

[0136] Phase compensation is performed on the time delay spectrum of at least some of the M symbols in the second data based on the phase difference.

[0137] The phase difference between the time delay spectra of the M symbols in the second data described above can be obtained through a reference path, phase construction, or group phase difference. For example, obtaining the phase difference between the time delay spectra of the M symbols in the second data described above includes the following:

[0138] The phase difference between the time delay spectra of the M symbols in the second data is obtained by means of a reference path.

[0139] The phase difference between the time delay spectra of the M symbols in the second data is obtained by phase construction method;

[0140] The phase difference between the time delay spectra of the M symbols in the second data is obtained by the group phase difference method.

[0141] In some embodiments, the step of performing phase compensation on the time delay spectrum of at least some of the M symbols in the second data based on the phase difference includes:

[0142] Based on the phase difference, a compensation vector is constructed for the time delay spectrum of at least some of the M symbols in the second data, and the time delay spectrum of at least some of the M symbols in the second data is compensated based on the compensation vector.

[0143] The aforementioned compensation vector includes time delay spectrum compensation elements for at least some of the symbols. Taking the compensation of the time delay spectrum of all M symbols as an example, the compensation vector can be constructed based on the obtained phase difference vector as follows: or The compensation values ​​correspond to M symbols respectively, where J represents the imaginary factor. Then, based on the compensation vector, phase compensation is performed on the time delay spectrum of at least some of the M symbols in the second data.

[0144] For example: the second data is a complex matrix with dimension P×M. The third data is also a complex matrix of dimension P×M, denoted as H. Then the element in the p-th (p=1,2,…,P)-th row and k-th (k=1,2,…,M)-th column of the third data H is... That is to Each row in the vector is multiplied pointwise by Φ (or, in other words, the Hadamard product).

[0145] For example: the second data is a complex matrix S = [s1, s2, ..., sm] with dimension N×M. M The third data is also a complex matrix of dimension N×M, denoted as Γ. Then the element in the nth (n=1,2,…,N) row and kth (k=1,2,…,M) column of the third data Γ is Γ(n,k)=S(n,k)Φ(k), which is to perform a pointwise multiplication (or Hadamard product) operation between each row of Γ and Φ.

[0146] In this embodiment, phase compensation is performed on the time delay spectrum of at least some of the M symbols in the second data according to the phase difference, which can effectively suppress the phase deviation and solve the phase deviation problem.

[0147] In some implementations, obtaining the phase difference between the time delay spectra of the M symbols in the second data via a reference path includes:

[0148] Obtain the phase of the unit corresponding to the reference path in the time delay spectrum of the M symbols in the second data, and calculate the phase difference between the time delay spectra of the M symbols in the second data based on the phase. The phase difference includes the difference between the phases corresponding to the M symbols, or the phase difference includes the difference between the phases corresponding to the M-1 symbols and the phase corresponding to the first symbol, where the first symbol is one of the M symbols and the M-1 symbols are the M-1 symbols other than the first symbol.

[0149] Wherein, the unit corresponding to the reference path in the time delay spectrum of the M symbols in the second data mentioned above may include the following:

[0150] The cell in the second data where the reference path is located on the time delay spectrum of the M symbols;

[0151] The cell corresponding to the mean of the cell index set;

[0152] The cell corresponding to the cell index that appears most frequently in the cell index set;

[0153] The cell index set includes the cell indices of the M symbols of the reference path in the second data on the time delay spectrum.

[0154] After the first processing step of time delay spectrum alignment The values ​​of (representing the cell indices of the reference path in the time delay spectrum over M symbols) are equal or similar, and need to be determined according to... The cell corresponding to the reference path in the second data on the time delay spectrum of the M symbols is denoted as... Used to determine the phase difference between the time delay spectra of each symbol.

[0155] Among them, When the values ​​are equal, the cell corresponding to the reference path in the time delay spectrum of the M symbols in the second data is directly the cell where the reference path is located in the time delay spectrum of the M symbols in the second data. For example, if the shift value is determined according to the cell index of the reference path in the time delay spectrum in the first process, then If all values ​​of are equal, then

[0156] For example, the reference paths on M symbols are denoted as {g1, g2, ..., g} in the time delay spectrum. M After alignment and time delay spectrum downsampling, g1, g2, ..., g M The values ​​of are equal, denoted as g. u =g1=g2=…=g M g uThe reference path in the second data is located in the time delay spectrum of the M symbols.

[0157] exist When the values ​​are equal or similar, the unit corresponding to the time delay spectrum of the M symbols in the reference path in the second data mentioned above is the unit corresponding to the mean of the unit index set or the unit corresponding to the unit index that appears most frequently in the unit index set.

[0158] For example: if the shift values ​​between time delay spectra are extracted through correlation operations in the first process, then The values ​​of are equal or very close. In this case, The determination method includes one of the following two:

[0159] Will After taking the mean, finding the integer closest to the mean (i.e., the round() operation) can be represented as: That is, the cell corresponding to the mean of the cell index set;

[0160] Will The most frequently repeated value in the middle is d u The value. For example, If there are 60 values ​​that are 170, 30 values ​​that are 171, and 10 values ​​that are 169, then the value with the most repetition, 170, is taken as... The value is the cell corresponding to the cell index that appears most frequently in the cell index set.

[0161] The phase of the unit corresponding to the reference path in the time delay spectrum of the M symbols in the second data obtained above can be obtained by... After the value of , then any k-th symbol in the th position The phase on each unit is By iterating through the values ​​of k, we can obtain the time delay spectrum on the M symbols at the th symbol. A vector consisting of the phase values ​​on each unit This allows us to obtain the phase difference between the time delay spectra of the second data over M symbols.

[0162] Alternatively, in obtaining the reference path of the M symbols mentioned in the second data, the cell g located on the time delay spectrum u After the value of , then any k-th symbol at the g-th position u The phase on each unit is ∠s k (g u By iterating through the values ​​of k, we can obtain the time delay spectrum on the g-th symbol of the M symbols. u The vector {∠s1(g)} is formed by the phase values ​​on each time delay resolution unit. u ),∠s2(g u ),…,∠sM (g u )}, that is, the phase difference between the time delay spectra of the second data over M symbols.

[0163] The above implementation can realize the phase difference between the time delay spectra of the M symbols in the second data based on the phase calculation of the reference path.

[0164] In some embodiments, obtaining the phase difference between the time delay spectra of the M symbols in the second data through phase construction includes:

[0165] The phase difference between the time delay spectra of the M symbols in the second data is constructed based on the shift information, wherein the shift information is the shift information between the time delay spectra of the M symbols in the first data.

[0166] The shift information mentioned above is explained in the corresponding description of the above implementation method, and will not be repeated here.

[0167] The phase difference between the time delay spectra of the M symbols in the second data constructed based on the shift information can be constructed by using the shift information between the time delay spectra of the M symbols in the first data to construct a phase vector.

[0168] For any k-th symbol, construct the phase vector based on the shift information between symbols. Where δ k This represents the shift information between the k-th symbol and the j-th symbol, or the shift information between the k-th symbol and the aforementioned first symbol. See the description of the above implementation method for details. Here, P is the number of points in the IDFT, and N is the number of subcarriers occupied by the sensed signal. The phase difference vector is obtained by iterating through k. This yields the phase difference between the time delay spectra of the M symbols in the second data.

[0169] In this embodiment, the phase difference between the time delay spectra of the M symbols in the second data can be constructed based on the shift information, thereby reducing computational overhead.

[0170] In some embodiments, the phase difference between the time delay spectra of the M symbols in the second data obtained by the group phase difference method includes:

[0171] The phase difference of the time delay spectrum between the j-th and k-th symbols among the M symbols in the second data. j is less than or equal to M, and k is less than or equal to M;

[0172] Wherein, the phase difference Includes the following:

[0173] The average of the phase differences between multiple units, wherein the phase differences between multiple units are the phase differences between multiple units in the time delay spectrum of the second data in the j-th and k-th symbols;

[0174] The phase value of the element whose index equals the shift information in the first correlation spectrum, wherein the shift information is the shift information between the time delay spectra of the j-th symbol and the k-th symbol in the first data, and the first correlation spectrum is the phase value of the element whose index equals the shift information in the first correlation spectrum. j and r k The correlation spectrum obtained by performing cyclic cross-correlation operation, wherein r j and r k These represent the time delay spectra of the j-th and k-th symbols of the first data in the M symbols, respectively;

[0175] The phase value of the element whose index is equal to the first value in the third correlation spectrum, wherein the third correlation spectrum is the correlation spectrum obtained by performing a cyclic cross-correlation operation on the time delay spectra of the second data at the j-th symbol and the k-th symbol.

[0176] The average phase difference between the above multiple units can be calculated for all P units, for all p = 1, 2, ..., P. Then, the mean of all P phase differences is calculated as the group phase difference, i.e. This yields the average phase difference between the aforementioned multiple units.

[0177] For example, for the second data sampled by a factor of P / N, for N time delay resolution units, for all n = 1, 2, ..., N, calculate the phase difference. Then, the mean of all N phase differences is calculated as the group phase difference, i.e. This yields the average phase difference between the aforementioned multiple units.

[0178] The phase value of the element indexed as shift information in the first correlation spectrum mentioned above can be used to determine the time delay spectrum r of the j-th OFDM symbol. j The time delay spectrum r of the k-th OFDM symbol k Perform cyclic cross-correlation to obtain the first correlation spectrum, and then use the index value of the first correlation spectrum as δ. k,j The phase value of the element is used as the group phase difference between the j-th symbol and the k-th symbol.

[0179] The aforementioned first value can be a protocol convention or a network-side device configuration; for example, the first value can be 0 or 1. For example, the delay spectrum for the j-th symbol. The time delay spectrum of the kth symbol A cyclic cross-correlation operation is performed to obtain the third correlation spectrum. Then, the phase value of the element with an index of 1 (counting from 1) in the third correlation spectrum is used as the group phase difference between the j-th symbol and the k-th symbol.

[0180] For example, when the second data is the data obtained after downsampling, the time delay spectrum s of the j-th OFDM symbol j The time delay spectrum of the k-th OFDM symbol s k A cyclic cross-correlation operation is performed to obtain the fourth correlation spectrum. Then, the phase value of the element with an index value of 1 (counting from 1) in the fourth correlation spectrum is used as the group phase difference between the j-th OFDM symbol and the k-th OFDM symbol.

[0181] It should be noted that in the embodiments of this application, s can represent the time delay spectrum when the second data is the data obtained after the alignment process and downsampling, while r can represent the time delay spectrum when the second data is the data obtained after the alignment process.

[0182] In the above embodiments, the phase difference between the time delay spectra of the M symbols in the second data can be obtained based on different methods to achieve different phase compensation effects. Figure 10 For example, Figure 10 For corresponding Figure 8 The effect of phase compensation in the second processing of the second data. Figure 10 In the diagram, (a) represents the phase deviation caused by timing drift before phase compensation. Figure 10 (b) in the middle Figure 10 In the diagram, (d) represents the phase difference determined by using a reference path, the phase difference constructed based on shift information, and the phase difference including the phase difference of the time delay spectrum of the j-th and k-th symbols among the M symbols mentioned in the second data. The remaining phase deviation after phase compensation. Figure 10 It can be seen that the embodiments of this application can effectively suppress phase deviation.

[0183] The processing methods provided by the above-described embodiments of this application are simple and intuitive to operate, and have a wide range of applications. For example, they can be used for single or multiple targets, and can be used with or without a line-of-sight (LOS) path between the transmitter and receiver sensing the signal. Furthermore, prototype testing results show that the data processing method proposed in this application can achieve near-perfect time-frequency synchronization.

[0184] In this embodiment, a first device performs a first process on first data to obtain second data. The first data is data corresponding to a sensing signal. The first process aligns the time delay spectra of M symbols in the first data, where M symbols are the M symbols occupied by the sensing signal, and M is an integer greater than 1. The first device then performs a second process on the second data to obtain third data. The second process performs phase compensation on the time delay spectra of at least some of the M symbols in the second data. Thus, the first process aligns the time delay spectra of the first data across the M symbols, solving the problem of time delay spectrum shift. The second process performs phase compensation on the time delay spectra of at least some of the M symbols in the second data, solving the problem of phase deviation. Furthermore, by resolving both phase deviation and time delay spectrum shift issues, the sensing results obtained from subsequent processing become more accurate.

[0185] The following uses OFDM symbol as an example to illustrate the method provided in the embodiments of this application through multiple examples:

[0186] Example 1:

[0187] In this embodiment, after aligning the time delay spectra of each OFDM symbol in the first processing step, no downsampling operation of the time delay spectrum is performed in subsequent processing. The advantage is that it is suitable for oversampling of time delay spectra that are not integer multiples, which facilitates faster processing of oversampled IDFT (or zero-padding IDFT) operations in hardware. Of course, the method of this embodiment can also be used for oversampling of time delay spectra that are integer multiples.

[0188] This embodiment includes the following two steps:

[0189] Step 1: The first device performs the first processing on the first data to align the time delay spectra of each OFDM symbol and outputs the second data (Step 1 can be called the "time delay spectrum alignment" operation).

[0190] Step 2: The first device performs a second processing on the second data to compensate for the phase deviation between each OFDM symbol and outputs the third data (Step 2 can be called the "phase compensation" operation).

[0191] In this embodiment, the first data has a dimension of N×M, and the second and third data have dimensions of P×M. M, N, and P are all positive integers, and P>N.

[0192] In some implementations, the first data is a time-frequency domain channel matrix with dimensions N×M, where N is the number of subcarriers occupied by the sensing signal and M is the number of OFDM symbols occupied by the sensing signal. That is, the first data includes M OFDM symbols, each OFDM symbol having N subcarriers, forming an N-row, M-column time-frequency domain channel matrix.

[0193] In some implementations, after receiving the signal, the receiver of the sensing signal (i.e., the first device mentioned above) obtains the first data through steps such as down-conversion, filtering, AD sampling, FFT operation and channel estimation.

[0194] Optionally, the channel estimation method is least squares channel estimation. That is, the sensed signal is transformed from the time domain to the frequency domain by an FFT operation to obtain a frequency domain signal, and then the frequency domain signal on each RE is divided by the known sensing signal modulation sequence to obtain the first data.

[0195] In some implementations, the first process includes the following steps:

[0196] Step 1-1: Perform oversampling IDFT or zero-padding IDFT on the first data.

[0197] Under normal circumstances, the sensing signal occupies N subcarriers on each OFDM symbol. Therefore, for the sensing signal of each OFDM symbol, the frequency domain sensing signal can be transformed to the time delay domain by using N-point IDFT.

[0198] This step proposes that for each OFDM symbol's sensed signal, a P-point IDFT is used to transform the sensed signal from the frequency domain to the time delay domain, where P > N. In implementation, the P-point IDFT can be achieved through oversampling IDFT or zero-padding IDFT. When the number of IDFT points is the same, oversampling IDFT and zero-padding IDFT are equivalent.

[0199] The advantage of oversampling IDFT (or zero-padding IDFT) is that it can achieve better apparent resolution performance compared to regular IDFT, with the apparent resolution of the time delay spectrum becoming N / P times that of regular IDFT.

[0200] The first intermediate result obtained after this step is the time-delay spectrum in the time-delay domain, with dimensions P×M. That is, the first intermediate result includes M OFDM symbols, and each OFDM symbol includes a time-delay spectrum with P points.

[0201] Corresponding to Figure 5The time delay spectrum in (a) is obtained by using oversampled IDFT (or zero-padding IDFT). The resulting time delay spectrum (i.e., the first intermediate result) is as follows: Figure 7 As shown. Figure 7 The horizontal axis represents the OFDM symbol index, and the vertical axis represents the apparent time delay resolution cell index. The number of OFDM symbols shown in the figure is M=100, and the number of IDFT points is P=8768. For ease of observation, the vertical axis in the figure only shows the range of 1 to 3200.

[0202] In some implementations, the determination of the IDFT point count (i.e., P) in the first process (step 1-1) described above can be achieved using the following two methods:

[0203] Method 1: According to a specified multiple: that is, according to a certain multiple α, combined with the number of subcarriers N, the number of IDFT points in the first processing is P = αN.

[0204] When using this method, a first table is pre-defined, containing at least one available α value and its corresponding index. For example, in one embodiment, the first table...

[0205] The advantage of using this method to determine the IDFT point count is that the improvement in apparent resolution performance is an integer multiple. For example, if the latency resolution using a conventional IDFT is Δτ, then the apparent resolution after using an oversampled IDFT (or zero-padded IDFT) is Δτ / α. Furthermore, after the first processing, the obtained second data can be downsampled, thereby reducing the amount of data required for subsequent processing.

[0206] It should be noted that a drawback of using this method to determine the IDFT point count is that the resulting IDFT point count P = αN may not necessarily accelerate the IDFT operation. In typical chips, for DFT or IDFT operations with points that are powers of 2 or 4, the operation can be accelerated using the Fast Fourier Transform.

[0207] If the number of subcarriers N of the sensing signal is not an integer power of 2, then the final P = αN will also not be an integer power of 2, which is detrimental to computational speedup. For example, if the first subcarrier of each of the 273 RBs in the NR protocol is used for the sensing signal, then the sensing signal will have N = 273 subcarriers, which is also detrimental to computational speedup.

[0208] Method 2: Obtain P directly according to the specified IDFT points: that is, obtain P directly according to the specified IDFT points.

[0209] When this method is used, a second table is pre-set, which contains at least one available P value and its corresponding index. For example, in one embodiment, the second table is shown in Table 3 above.

[0210] In contrast to the drawbacks of the previous method for determining IDFT points, this method has the advantage of ensuring that the final IDFT point value is a power of 2 or a power of 4, thereby accelerating the computation.

[0211] It should be noted that if the multiple P / N is not an integer, it is impossible to downsample the second data obtained after the first processing or the third data obtained after the second processing, thereby reducing the amount of data for subsequent processing.

[0212] Of course, if the multiple P / N is not an integer, the time delay-Doppler spectrum of the second or third data can be transformed back to the frequency domain by performing a P-point DFT operation along the time delay dimension. Then, only N points are retained in the frequency domain, and then an N-point IDFT operation is performed along the frequency domain to obtain the downsampled time delay spectrum.

[0213] In some embodiments, the first process described above further includes:

[0214] Step 1-2: Extract the shift values ​​between the time delay spectra of each OFDM symbol.

[0215] Based on the "stop-hop" assumption in radar theory, it can be assumed that the positions of all reflectors, including the background environment and the target being sensed, remain unchanged across all OFDM symbols within a coherent processing time range. Therefore, the envelope of the time delay spectrum on each OFDM symbol should be the same. However, due to timing drift, the time delay spectra on each OFDM symbol will shift, and this step aims to extract this cyclic shift value.

[0216] like Figure 11 As shown, this corresponds to Figure 7 The time delay spectra on the first and sixth OFDM symbols are cyclically shifted by 23 apparent time delay spectrum resolution units.

[0217] In some implementations, the method for extracting the shift values ​​between the time delay spectra of the various OFDM symbols can be one of the following two methods:

[0218] Reference path method: Based on the apparent time delay resolution cell index of the reference path in the time delay spectrum, the apparent time delay resolution cell index corresponding to the reference path in the time delay spectrum of each OFDM symbol is extracted. The difference between the extracted apparent time delay resolution cell indices is the shift value between the time delay spectra of each OFDM symbol.

[0219] Under normal circumstances, the diameter with the strongest power is selected as the reference diameter.

[0220] Specifically, the apparent time delay resolved cell indices corresponding to the reference paths on the M OFDM symbols in the time delay spectrum are denoted as {d1, d2, ..., d...}. M}, then the shift value between the time delay spectra of the j-th OFDM symbol and the k-th OFDM symbol is δ. k,j =d k -d j .

[0221] When the signal-to-noise ratio is good, the shift value of the time delay spectrum extracted by this method will be more accurate; when the signal-to-noise ratio is poor, the shift value of the extracted time delay spectrum may have some error.

[0222] In some implementations, one OFDM symbol can be selected from M OFDM symbols as a reference, and the shift values ​​of the time delay spectra of the other M-1 OFDM symbols relative to the time delay spectrum of that OFDM symbol can be calculated; that is, a value of j is fixed, and then the values ​​of k are iterated to calculate δ using the above method. k,j At this time, δ k,j The 'j' in the equation can be omitted, becoming 'δ'. k Obviously, there is δ k＝j =0.

[0223] In some implementations, the shift values ​​of the time delay spectrum of the other M-1 OFDM symbols can be calculated using the first OFDM symbol as a reference.

[0224] Group delay method: The shift values ​​between delay spectra are extracted through cross-correlation operations. The delay spectra of the j-th OFDM symbol and the k-th OFDM symbol are denoted as r. j and r k Obviously r j and r k Both are complex vectors of size P×1; through r j and r k The correlation operation between them can extract the shift value δ between them. k,j .

[0225] The specific method is as follows: for r j and r k Perform cyclic cross-correlation to obtain the first correlation spectrum, or perform |r j |and|r k The second correlation spectrum is obtained by performing a cyclic cross-correlation operation. Clearly, both the first and second correlation spectra are complex vectors of size P×1. Therefore, the index value corresponding to the maximum amplitude value of either the first or second correlation spectrum is r. j and r k The shift value δ between k,j .

[0226] In some implementations, one OFDM symbol can be selected from M OFDM symbols as a reference, and the shift values ​​of the time delay spectra of the other M-1 OFDM symbols relative to the time delay spectrum of that OFDM symbol can be calculated; that is, a value of j is fixed, and then the values ​​of k are iterated to calculate δ using the above method. k,j At this time, δ k,j The 'j' in the equation can be omitted, becoming 'δ'. k Obviously, there is δ k＝j =0.

[0227] In some implementations, the shift values ​​of the time delay spectrum of the other M-1 OFDM symbols can be calculated using the first OFDM symbol as a reference.

[0228] In some embodiments, the first process described above further includes:

[0229] Steps 1-3: Based on the shift value of the extracted time delay spectrum, perform reverse cyclic shift of the time delay spectrum to achieve alignment between the time delay spectra on each OFDM symbol. The result is the second data, with a dimension of P×M.

[0230] After obtaining all shift values ​​δ k After k = 1, 2, ..., M, perform δ calculation on the time delay spectrum of the k-th OFDM symbol. k Reverse cyclic shift of each apparent time delay resolution unit.

[0231] Here, "reverse" refers to the polarity of the shifts between the individual OFDM symbols. For example, if δ k If the value is a positive integer, it means that the delay spectrum of the k-th OFDM symbol has been shifted relative to the reference (the delay spectrum of the j-th OFDM symbol) along the direction in which the delay resolution cell index increases; therefore, the reverse cyclic shift is to perform a δ shift on the delay spectrum of the k-th OFDM symbol along the direction in which the delay resolution cell index decreases. k The shift of an apparent time delay resolution unit. Conversely, if δ k If the value is a negative integer, it means that the delay spectrum of the k-th OFDM symbol has been shifted relative to the reference (the delay spectrum of the j-th OFDM symbol) along the direction in which the delay resolution cell index decreases; therefore, the reverse cyclic shift is to shift the delay spectrum of the k-th OFDM symbol along the direction in which the delay resolution cell index increases by |δ k | The shift of an apparent time delay resolution unit.

[0232] According to the above method, corresponding to Figure 7 The time delay spectrum, the second data obtained is as follows Figure 8 As shown.

[0233] In some implementations, the second process described above includes:

[0234] Step 2-1: For the second data, obtain the phase difference between the time delay spectra of each OFDM symbol.

[0235] The time delay spectra of the j-th OFDM symbol and the k-th OFDM symbol in the second data obtained after the first processing are denoted as follows: and For any p-th (p = 1, 2, ..., P) apparent time delay resolution unit, its... and The phase difference between them is caused by carrier frequency deviation, timing drift, and random phase, denoted as . Where ∠ represents the phase calculation. Within the time range of any OFDM symbol, the carrier frequency offset, timing drift, and random phase can be considered constant. Therefore, it can be assumed that for all p = 1, 2, ..., P, They are all the same; that is The value of is independent of p, and depends only on j and k.

[0236] If the j-th OFDM symbol is set as the reference, then the phase difference between M OFDM symbols can be determined. If we further omit the subscript j, the phase difference between M OFDM symbols can be expressed as:

[0237] In some implementations, the method for obtaining the phase difference between the time delay spectra of the M OFDM symbols may include one of the following three:

[0238] Reference path method: Based on the phase of the apparent time delay resolution cell where the reference path is located in the time delay spectrum, that is, the apparent time delay resolution cell corresponding to the reference path in the time delay spectrum of each OFDM symbol is extracted in the second data, and then the corresponding phase value is obtained; then, the difference between the obtained phase values ​​is the phase difference between the time delay spectra of each OFDM symbol. Generally, the path with the strongest power is used as the reference path. Specifically, it includes the following methods:

[0239] The apparent time delay resolved unit corresponding to the reference paths on the M OFDM symbols in the time delay spectrum is denoted as... After the first processing step of time delay spectrum alignment... The values ​​are equal or very close. It needs to be determined based on... Define a value, denoted as Used to determine the phase difference between the time delay spectra of each OFDM symbol. The determination includes the following situations:

[0240] If the shift value is determined in the first process based on the apparent time delay resolution cell index of the reference path on the time delay spectrum (i.e., the reference path method in (1) of 6), then If all values ​​of are equal, then

[0241] If the shift values ​​between time delay spectra are extracted through correlation operations in the first process (i.e., the group delay method), then The values ​​of are equal or very close. In this case, The determination method includes one of the following two:

[0242] Will After taking the mean, finding the integer closest to the mean (i.e., the round() operation) can be represented as:

[0243] Will The most frequently repeated value in the middle is d u The value. For example, If there are 60 values ​​that are 170, 30 values ​​that are 171, and 10 values ​​that are 169, then the value with the most repetition, 170, is taken as... The value of .

[0244] In obtaining After the value, the k-th OFDM symbol at the th The phase of each view in the time delay resolution unit is By iterating through the possible values ​​of k, we can obtain the time delay spectrum on the M OFDM symbols at the th... A vector consisting of the phase values ​​of each view on the time-delay resolution unit

[0245] In some implementations, one OFDM symbol can be selected from M OFDM symbols as a reference, and the phase difference between the time delay spectra of the other M-1 OFDM symbols and the time delay spectrum of that OFDM symbol can be calculated. That is, a value j is determined, and then the values ​​of k are iterated to calculate the phase difference at the 1st... The phase difference between the time delay spectrum of the k-th OFDM symbol and the time delay spectrum of the j-th OFDM symbol in the time delay resolution unit. at this time, The 'j' in the text can be omitted, becoming Obviously there is

[0246] In some implementations, the phase difference of the time delay spectrum of the other M-1 OFDM symbols can be calculated using the first OFDM symbol as a reference.

[0247] The method described above determines the phase difference between the time delay spectra of each OFDM symbol based on the strongest path. It's easy to understand that the same method can also be used to determine several strongest paths and then individually determine the phase difference vector. Then, the average value is calculated to obtain the final phase difference vector.

[0248] Phase construction method: Construct a phase vector based on the shift values ​​between each OFDM symbol in the first intermediate result.

[0249] For any k-th OFDM symbol, construct the phase vector based on the shift values ​​between all OFDM symbols as follows: The meanings of each parameter are explained in the preceding text. The phase difference vector is obtained by iterating through the values ​​of k.

[0250] Group phase difference method: Based on the first intermediate result or the second data, extract the group phase difference between the time delay spectra of each OFDM symbol.

[0251] Specifically, to calculate the group phase difference between the j-th OFDM symbol and the k-th OFDM symbol, the following two methods are used:

[0252] For the second data, the following calculation is performed: For P apparent time delay resolution units, for all p = 1, 2, ..., P, the phase difference is calculated. Then, the mean of all P phase differences is calculated as the group phase difference, i.e.

[0253] For the first intermediate result, the following calculation is performed: the time delay spectrum r of the j-th OFDM symbol j The time delay spectrum r of the k-th OFDM symbol k Perform cyclic cross-correlation to obtain the first correlation spectrum (same as in 6(2)), and then use the index value of the first correlation spectrum as δ. k,j The phase value of the element is used as the group phase difference between the j-th OFDM symbol and the k-th OFDM symbol. This includes one of the following two situations:

[0254] First correlation spectrum and index value δ k,j The group phase difference has already been calculated above; in this case, no additional calculations are required to determine it directly.

[0255] Index value δ k,j The index value δ, which was previously calculated but not previously calculated, corresponds to the index value δ obtained from the second correlation spectrum. k,j In this case, it is necessary to calculate the first correlation spectrum and then, based on the previously determined index value δ, proceed.k,j That will confirm

[0256] For the second data, the following calculation is performed: the time delay spectrum of the j-th OFDM symbol. The time delay spectrum of the k-th OFDM symbol A cyclic cross-correlation operation is performed to obtain the third correlation spectrum. Then, the phase value of the element with an index value of 1 (counting from 1) in the third correlation spectrum is used as the group phase difference between the j-th OFDM symbol and the k-th OFDM symbol.

[0257] Of the three methods for determining the phase compensation vector mentioned above, the group phase difference method is the most universally applicable method, suitable for situations with carrier frequency deviation, timing drift, and random phase, and also suitable for situations without significantly strong paths; the reference path method is suitable for situations with one or more strong paths, and also suitable for situations with carrier frequency deviation, timing drift, and random phase; the phase construction method is suitable for situations without random phase, and also suitable for situations with carrier frequency deviation and timing drift, and also suitable for situations without significantly strong paths.

[0258] In some embodiments, the second process further includes:

[0259] Step 2-2: Perform phase compensation on the time delay spectrum of each OFDM symbol in the second data according to the extracted phase vector to obtain the third data, which has a dimension of P×M.

[0260] First, construct the following compensation vector based on the obtained phase difference vector: or Here, 'J' represents the imaginary factor. Which of the two forms the compensation vector uses depends on the specific circumstances.

[0261] The second data is a complex matrix of dimension P×M. The third data is also a complex matrix of dimension P×M, denoted as H. Then the element in the p-th (p=1,2,…,P)-th row and k-th (k=1,2,…,M)-th column of the third data H is... That is to Each row in the vector is multiplied by Φ using a dot product (or a Hadamard product).

[0262] For specific effects, please refer to the above. Figure 10 The effect shown.

[0263] Example 2:

[0264] In this embodiment, after aligning the time delay spectra of each OFDM symbol in the first process, a downsampling operation of the time delay spectrum is performed before subsequent processing. The advantage is that it reduces the amount of data in subsequent processing within the time delay dimension. Obviously, this embodiment is only applicable to cases where integer multiples of the time delay spectrum are oversampled in the first process.

[0265] This embodiment includes the following two steps:

[0266] Step 1: The first device performs first processing on the first data to align the time delay spectra of each OFDM symbol, and downsamples the time delay spectrum to output the second data;

[0267] Step 2: The first device performs a second processing on the second data to compensate for the phase difference between each OFDM symbol and outputs the third data.

[0268] In this embodiment, the first data has a dimension of N×M, and the second and third data have dimensions of P×M. M, N, and P are all positive integers, and P>N.

[0269] The alignment of the time delay spectra of each OFDM symbol in the first process is described in the above embodiment 1. Specifically, refer to steps 1-1 to 1-3 in the embodiment, which will not be repeated here.

[0270] In some embodiments, the first process described above further includes:

[0271] Steps 1-4: The data obtained from the alignment process is downsampled along the time delay dimension by a factor of α = P / N to obtain the second data, which has a dimension of N×M. This restores the time delay spectrum to the state without sampling.

[0272] According to the above method, corresponding to Figure 8 The fourth data obtained after downsampling the time delay spectrum is as follows: Figure 9 As shown in the figure, the horizontal axis represents the OFDM symbol index, and the vertical axis represents the time delay cell index of the downsampled time delay spectrum.

[0273] In some implementations, the second process described above includes:

[0274] Step 2-1: For the second data, obtain the phase difference between the time delay spectra of each OFDM symbol.

[0275] The time delay spectra of the j-th OFDM symbol and the k-th OFDM symbol in the second data obtained after the first processing are denoted as s, respectively. j and s k For any nth (n = 1, 2, ..., N) time-delay resolution unit, its time delay is s jThe phase difference between and sk is caused by carrier frequency deviation, timing drift, and random phase, denoted as . Where ∠ represents the phase calculation. Within the time range of any OFDM symbol, the carrier frequency deviation, timing drift, and random phase can be considered constant. Therefore, it can be assumed that for all n = 1, 2, ..., N, They are all the same; that is The value of is independent of n, and depends only on j and k.

[0276] If the j-th OFDM symbol is set as the reference, then the phase difference between M OFDM symbols can be determined. If we further omit the subscript j, the phase difference between M OFDM symbols can be expressed as:

[0277] In some implementations, the method for obtaining the phase difference between the time delay spectra of the M OFDM symbols may include one of the following three:

[0278] Reference path method: Based on the phase of the time delay resolution cell where the reference path is located in the time delay spectrum, that is, extracting the time delay resolution cell corresponding to the reference path in the time delay spectrum of each OFDM symbol from the fourth data, and then obtaining the corresponding phase value; then, the difference between the obtained phase values ​​is the phase difference between the time delay spectra of each OFDM symbol. Generally, the path with the strongest power is used as the reference path. Specifically, it includes the following methods:

[0279] The apparent time delay resolvable cells corresponding to the reference paths on the M OFDM symbols in the time delay spectrum are denoted as {g1, g2, ..., g...} M After the first processing step of time delay spectrum alignment and time delay spectrum downsampling, g1, g2, ..., g M The values ​​of are equal, denoted as g. u =g1=g2=…=g M .

[0280] In obtaining g u After the value, the value of any k-th OFDM symbol at the g-th position... u The phase on each time delay resolution unit is ∠s k (g u By iterating through the values ​​of k, the time delay spectrum on the M OFDM symbols at the g-th position can be obtained. u The vector {∠s1(g)} is formed by the phase values ​​on each time delay resolution unit. u ),∠s2(g u ),…,∠s M (g u )}.

[0281] In some implementations, one OFDM symbol can be selected from M OFDM symbols as a reference, and the phase difference between the time delay spectra of the other M-1 OFDM symbols and the time delay spectrum of that OFDM symbol can be calculated. That is, a value j is determined, and then the values ​​of k are iterated to calculate the phase difference at the g-th OFDM symbol. u The phase difference between the time delay spectrum of the k-th OFDM symbol and the time delay spectrum of the j-th OFDM symbol in the time delay resolution unit. at this time, The 'j' in the text can be omitted, becoming Obviously there is

[0282] In some implementations, the phase difference of the time delay spectrum of the other M-1 OFDM symbols can be calculated using the first OFDM symbol as a reference.

[0283] The method described above determines the phase difference between the time delay spectra of each OFDM symbol based on the strongest path. It's easy to understand that the same method can also be used to determine several strongest paths and then individually determine the phase difference vector. Then, the average value is calculated to obtain the final phase difference vector.

[0284] Phase construction method: Construct a phase vector based on the shift values ​​between each OFDM symbol in the first intermediate result.

[0285] For any k-th OFDM symbol, construct the phase vector based on the shift values ​​between all OFDM symbols as follows: The meanings of each parameter are explained in the preceding text. The phase compensation vector is obtained by iterating through the values ​​of k.

[0286] Group phase difference method: Based on the first intermediate result or the fourth data, extract the group phase difference between the time delay spectra of each OFDM symbol.

[0287] To calculate the group phase difference between the j-th and k-th OFDM symbols, the following two methods are used:

[0288] For the fourth data point, the following calculation is performed: For N time delay resolution units, for all n = 1, 2, ..., N, calculate the phase difference. Then, the mean of all N phase differences is calculated as the group phase difference, i.e.

[0289] For the first intermediate result, the following calculation is performed: the time delay spectrum r of the j-th OFDM symbol j The time delay spectrum r of the k-th OFDM symbol k Perform cyclic cross-correlation to obtain the first correlation spectrum, and then use the index value of the first correlation spectrum as δ.k,j The phase value of the element is used as the group phase difference between the j-th OFDM symbol and the k-th OFDM symbol. This includes one of the following two situations:

[0290] First correlation spectrum and index value δ k,j The group phase difference has already been calculated above; in this case, no additional calculations are required to determine it directly.

[0291] Index value δ k,j The index value δ, which was previously calculated but not previously calculated, corresponds to the index value δ obtained from the second correlation spectrum. k,j In this case, it is necessary to calculate the first correlation spectrum and then, based on the previously determined index value δ, proceed. k,j That will confirm

[0292] For the fourth data point, the following calculation is performed: the time delay spectrum s of the j-th OFDM symbol. j The time delay spectrum of the k-th OFDM symbol s k A cyclic cross-correlation operation is performed to obtain the fourth correlation spectrum. Then, the phase value of the element with an index value of 1 (counting from 1) in the fourth correlation spectrum is used as the group phase difference between the j-th OFDM symbol and the k-th OFDM symbol.

[0293] Of the three methods for determining the phase compensation vector mentioned above, the group phase difference method is the most universally applicable method, suitable for situations with carrier frequency deviation, timing drift, and random phase, and also suitable for situations without significantly strong paths; the reference path method is suitable for situations with one or more strong paths, and also suitable for situations with carrier frequency deviation, timing drift, and random phase; the phase construction method is suitable for situations without random phase, and also suitable for situations with carrier frequency deviation and timing drift, and also suitable for situations without significantly strong paths.

[0294] In some embodiments, the second process described above further includes:

[0295] Step 2-2: Perform phase compensation on the time delay spectrum of each OFDM symbol in the second data according to the extracted phase vector to obtain the third data, which has a dimension of N×M.

[0296] First, construct the following compensation vector based on the obtained phase difference vector: or Here, 'J' represents the imaginary factor. Which of the two forms the compensation vector uses depends on the specific circumstances.

[0297] The second data is a complex matrix S = [s1, s2, ..., sm] of dimension N×M. M The third data is also a complex matrix of dimension N×M, denoted as Γ. Then the element in the nth (n=1,2,…,N) row and kth (k=1,2,…,M) column of the third data Γ is Γ(n,k)=S(n,k)Φ(k); that is, the dot product (or Hadamard product) operation is performed between each row of Γ and Φ.

[0298] The effect of phase compensation after the second process in this embodiment is the same as that in embodiment one. Figure 10 Similar examples are shown here, so they will not be repeated.

[0299] Example 3:

[0300] This embodiment mainly describes the downsampling method.

[0301] In Embodiments 1 and 2 above, the second data in Embodiment 2 is obtained by downsampling the data from the alignment process in Embodiment 1 by a factor of α = P / N in the time delay dimension. Therefore, the second processing in Embodiment 2, as well as other signal processing after the second processing (e.g., signal detection), will have a smaller data volume. This is the main difference between Embodiments 1 and 2.

[0302] When α = P / N is an integer, the second data can be obtained by directly downsampling the aligned data along the time delay dimension.

[0303] If α = P / N is not an integer, downsampling can be performed using the following steps:

[0304] For each OFDM symbol (P sample points), the second data is transformed into the frequency domain by performing a P-point DFT transformation along the time delay dimension;

[0305] For each OFDM symbol (P sample points), only N sample points are retained in the frequency domain (i.e., the 1st, 2nd, 3rd...Nth);

[0306] For each OFDM symbol (N sample points), perform an N-point IDFT transform along the frequency dimension to the time delay domain to obtain the downsampled second data.

[0307] Example 4:

[0308] This embodiment mainly describes the specific application of the embodiments of this application.

[0309] The algorithm proposed in this application is applicable to all sensing applications that require signal processing of sensing signals from multiple OFDM symbols to obtain sensing results. Typical applications include the following types:

[0310] Passive sensing target localization applications

[0311] A typical signal processing method involves processing the sensing signals of M OFDM symbols to obtain the time-delay-Doppler spectrum, and then performing target detection and parameter estimation from the time-delay-Doppler spectrum. For bistatic sensing, timing drift causes time-delay spectrum shifts and phase deviations between OFDM symbols; in some cases, random phase deviations may also exist. If methods from traditional radar technology are directly used, the obtained time-delay-Doppler spectrum will be as follows: Figure 5 As shown in (b), severe time-delay Doppler spectral dispersion occurs, leading to the inability to accurately detect and estimate parameters of the target.

[0312] After processing using the method provided in this application, the second data can be subjected to FFT along the time dimension (the dimension of the OFDM symbol index) to obtain a non-dispersion (or very weakly dispersion) time-delay-Doppler spectrum, which can then be used for subsequent detection of sensing targets and parameter estimation.

[0313] Frequency detection applications

[0314] A typical signal processing method involves processing the sensing signals of M OFDM symbols. This involves performing spectral analysis along the time dimension (the dimension of the OFDM symbol index) on the frequency domain channel state information or time delay spectrum of the M OFDM symbols to extract information such as respiratory rate and heart rate. However, in bistatic sensing, timing drift causes time delay spectrum shifts and phase deviations between OFDM symbols; in some cases, random phase shifts may also occur. Direct spectral analysis would yield incorrect spectra, making it impossible to extract the relevant information.

[0315] After processing using the method provided in this application, the obtained second data is subjected to spectral analysis along the time dimension (the dimension of the OFDM symbol index); or the second data is subjected to a DFT transform along the time delay dimension and returned to the frequency domain, and then spectral analysis is performed along the time dimension (the dimension of the OFDM symbol index). This yields the correct spectrum, enabling subsequent detection of sensing targets and parameter estimation.

[0316] The embodiments of this application achieve time delay spectrum alignment through a first process and phase compensation between OFDM symbols through a second process, thereby overcoming the problems of time delay spectrum shift and phase drift caused by timing drift. Furthermore, it can also overcome the problems of carrier frequency deviation and / or random phase. Thus, it solves the problem of time delay-Doppler spectrum dispersion caused by timing drift and / or random phase in bi-station sensing. Data processing using the method provided in the embodiments of this application can achieve performance approaching perfect time-frequency synchronization.

[0317] The data processing method provided in this application can be executed by a data processing device. This application uses an example of a data processing device executing the data processing method to illustrate the data processing device provided in this application.

[0318] This application provides a data processing apparatus. As an example, the data processing apparatus may be a communication device or a component within a communication device, such as a chip. The communication device may be a terminal, a network-side device, or a server, etc. Exemplarily, the terminal may include, but is not limited to, the type of terminal 11 listed above, and the network-side device may include, but is not limited to, the type of network-side device 12 listed above. This application does not impose specific limitations.

[0319] The data processing device may include a receiving module, a transmitting module, and a processing module. These modules can be implemented in software or hardware. When implemented in hardware, the processing module can be implemented by a processor. For example, the processor may include a general-purpose processor, a special-purpose processor, such as a Central Processing Unit (CPU), a microprocessor, a Digital Signal Processor (DSP), an Artificial Intelligence (AI) processor, a Graphics Processing Unit (GPU), an Application Specific Integrated Circuit (ASIC), a Network Processor (NP), a Field Programmable Gate Array (FPGA), or other programmable logic devices, gate circuits, transistors, discrete hardware components, etc. The receiving and transmitting modules may be implemented by a communication interface, which may include one or more of the following: a transceiver, pins, circuits, a bus, and a radio frequency unit.

[0320] For details, see Figure 12 When the data processing device is a terminal or a component within a terminal, or when the data processing device is a network-side device or a component within a network-side device, the data processing device 1200 includes:

[0321] The processing module 1201 is used to perform a first processing on the first data to obtain the second data. The first data is the data corresponding to the sensing signal. The first processing is used to align the time delay spectrum of M symbols in the first data. The M symbols are the M symbols occupied by the sensing signal, and M is an integer greater than 1.

[0322] The processing module 1201 is further configured to perform a second processing on the second data to obtain third data, wherein the second processing is used to perform phase compensation on the time delay spectrum of at least some of the M symbols in the second data.

[0323] Optionally, the processing module 1201 is used to perform a P-point inverse discrete Fourier transform (IDFT) on the first data to obtain the time delay spectrum of the M symbols in the first data, where P is an integer greater than N and N is the number of subcarriers occupied by the sensing signal; and to perform alignment processing on the time delay spectrum of the M symbols in the first data.

[0324] That is, the first process mentioned above includes:

[0325] Perform a P-point IDFT on the first data to obtain the time delay spectrum of the M symbols in the first data, where P is an integer greater than N and N is the number of subcarriers occupied by the sensing signal;

[0326] The time delay spectra of the M symbols in the first data are aligned.

[0327] Optionally, the processing module 1201 is configured to perform a P-point inverse discrete Fourier transform (IDFT) on the first data to obtain the time delay spectrum of the M symbols in the first data, where P is an integer greater than N and N is the number of subcarriers occupied by the sensing signal; and to obtain shift information between the time delay spectra of the M symbols in the first data; and to perform a reverse cyclic shift on the time delay spectrum of at least some of the M symbols in the first data according to the shift information, wherein the reverse cyclic shift is used to align the time delay spectra of the M symbols in the first data.

[0328] That is, the above-mentioned alignment process of the time delay spectrum of the M symbols in the first data includes:

[0329] Obtain the shift information between the time delay spectra of the M symbols in the first data;

[0330] The time delay spectrum of at least some of the M symbols in the first data is reverse cyclically shifted according to the shift information, and the reverse cyclic shift is used to align the time delay spectrum of the M symbols in the first data.

[0331] Optionally, the processing module 1201 is used to obtain the shift information between the time delay spectra of the M symbols in the first data via a reference path method; or

[0332] The processing module 1201 is used to obtain the shift information between the delay spectra of the M symbols in the first data through a group delay method.

[0333] Optionally, the processing module 1201 is used to obtain the cell index of the reference path in the first data on the time delay spectrum of the M symbols, and calculate the shift information based on the cell index. The shift information includes the difference between the cell indices corresponding to the M symbols, or the shift information includes the difference between the cell index corresponding to the M-1 symbols and the cell index corresponding to the first symbol.

[0334] That is, obtaining the shift information between the time delay spectra of the M symbols in the first data through the reference path method includes:

[0335] Obtain the cell index of the reference path in the first data on the time delay spectrum of the M symbols, and calculate the shift information based on the cell index. The shift information includes the difference between the cell indices corresponding to the M symbols, or the shift information includes the difference between the cell index corresponding to the M-1 symbols and the cell index corresponding to the first symbol.

[0336] Optionally, the processing module 1201 is configured to calculate the correlation spectrum between the second symbol and the first symbol based on the time delay spectrum of the M symbols in the first data, wherein the shift information includes the cell index corresponding to the maximum amplitude value in the correlation spectrum between the second symbol and the first symbol; and to calculate the correlation spectrum between the M-1 symbols and the first symbol based on the time delay spectrum of the M symbols in the first data, wherein the shift information includes the cell index corresponding to the maximum amplitude value in the correlation spectrum between the M-1 symbols and the first symbol.

[0337] Wherein, the first symbol is one of the M symbols, the M-1 symbols are the M-1 symbols other than the first symbol among the M symbols, and the second symbol is one of the M symbols other than the first symbol.

[0338] That is, obtaining the shift information between the delay spectra of the M symbols in the first data through the group delay method includes:

[0339] The correlation spectrum between the second symbol and the first symbol is calculated based on the time delay spectrum of the M symbols in the first data, and the shift information includes the cell index corresponding to the maximum amplitude value in the correlation spectrum between the second symbol and the first symbol;

[0340] Based on the time delay spectrum of the M symbols in the first data, the correlation spectrum of M-1 symbols with the first symbol is calculated respectively, and the shift information includes the cell index corresponding to the maximum amplitude value in the correlation spectrum of the M-1 symbols with the first symbol respectively;

[0341] Wherein, the first symbol is one of the M symbols, the M-1 symbols are the M-1 symbols other than the first symbol among the M symbols, and the second symbol is one of the M symbols other than the first symbol.

[0342] Optionally, the correlation spectrum includes:

[0343] For r j and r k The first correlation spectrum obtained by performing cyclic cross-correlation, or the correlation spectrum obtained by |r j |and|r k The second correlation spectrum obtained by performing cyclic cross-correlation operation, wherein the r j and r k Represent the time delay spectra of two symbols out of the M symbols in the first data, |r j |and|r k | represents the amplitude value of the time delay spectrum of the two symbols respectively.

[0344] Optionally, the second data is the data obtained from the alignment process; or

[0345] The processing module 1201 is further configured to downsample the aligned data along the time delay dimension by a factor of P / N, wherein the second data is the data obtained after downsampling.

[0346] That is, the first process mentioned above also includes:

[0347] The aligned data is downsampled by a factor of P / N along the time delay dimension, and the second data is the data obtained after the downsampling.

[0348] Optionally, P equals α × N, where α is an integer obtained based on a first table, the first table including at least one index and at least one value of α;

[0349] Alternatively, P can be an integer obtained based on a second table, which includes at least one index and at least one value of P.

[0350] Optionally, the processing module 1201 is used to obtain the phase difference between the time delay spectra of the M symbols in the second data; and to perform phase compensation on the time delay spectra of at least some of the M symbols in the second data according to the phase difference.

[0351] That is, the second process mentioned above includes:

[0352] Obtain the phase difference between the time delay spectra of the M symbols in the second data;

[0353] Phase compensation is performed on the time delay spectrum of at least some of the M symbols in the second data based on the phase difference.

[0354] Optionally, the processing module 1201 is used to obtain the phase difference between the time delay spectra of the M symbols in the second data using a reference path method; or

[0355] The processing module 1201 is used to obtain the phase difference between the time delay spectra of the M symbols in the second data through a phase construction method; or

[0356] The processing module 1201 is used to obtain the phase difference between the time delay spectra of the M symbols in the second data by means of group phase difference.

[0357] Optionally, the processing module 1201 is used to obtain the phase of the unit corresponding to the reference path in the time delay spectrum of the M symbols in the second data, and calculate the phase difference between the time delay spectra of the M symbols in the second data based on the phase. The phase difference includes the difference between the phases corresponding to the M symbols, or the phase difference includes the difference between the phases corresponding to the M-1 symbols and the phase corresponding to the first symbol. The first symbol is one of the M symbols, and the M-1 symbols are the M-1 symbols other than the first symbol.

[0358] That is, the phase difference between the time delay spectra of the M symbols in the second data obtained by the reference path method as described above includes:

[0359] Obtain the phase of the unit corresponding to the reference path in the time delay spectrum of the M symbols in the second data, and calculate the phase difference between the time delay spectra of the M symbols in the second data based on the phase. The phase difference includes the difference between the phases corresponding to the M symbols, or the phase difference includes the difference between the phases corresponding to the M-1 symbols and the phase corresponding to the first symbol, where the first symbol is one of the M symbols and the M-1 symbols are the M-1 symbols other than the first symbol.

[0360] The unit corresponding to the reference path in the time delay spectrum of the M symbols in the second data includes the following:

[0361] The cell in the second data where the reference path is located on the time delay spectrum of the M symbols;

[0362] The cell corresponding to the mean of the cell index set;

[0363] The cell corresponding to the cell index that appears most frequently in the cell index set;

[0364] The cell index set includes the cell indices of the reference path in the second data on the time delay spectrum of the M symbols.

[0365] Optionally, the processing module 1201 is used to construct the phase difference between the time delay spectra of the M symbols in the second data based on the shift information, wherein the shift information is the shift information between the time delay spectra of the M symbols in the first data.

[0366] That is, the phase difference between the time delay spectra of the M symbols in the second data obtained by the phase construction method described above includes:

[0367] The phase difference between the time delay spectra of the M symbols in the second data is constructed based on the shift information, wherein the shift information is the shift information between the time delay spectra of the M symbols in the first data.

[0368] Optionally, the phase difference between the time delay spectra of the M symbols in the second data obtained by the group phase difference method includes:

[0369] The phase difference of the time delay spectrum between the j-th and k-th symbols among the M symbols in the second data. j is less than or equal to M, and k is less than or equal to M;

[0370] Wherein, the phase difference Includes the following:

[0371] The average of the phase differences between multiple units, wherein the phase differences between multiple units are the phase differences between multiple units in the time delay spectrum of the second data in the j-th and k-th symbols;

[0372] The phase value of the element whose index equals the shift information in the first correlation spectrum, wherein the shift information is the shift information of the first data between the time delay spectra of the j-th and k-th symbols, and the first correlation spectrum is the phase value of the element whose index equals the shift information in the first correlation spectrum. j and r k The correlation spectrum obtained by performing cyclic cross-correlation operation, wherein r j and r k These represent the time delay spectra of the j-th and k-th symbols of the first data in the M symbols, respectively;

[0373] The phase value of the element whose index is equal to the first value in the third correlation spectrum, wherein the third correlation spectrum is the correlation spectrum obtained by performing a cyclic cross-correlation operation on the time delay spectra of the second data at the j-th symbol and the k-th symbol.

[0374] Optionally, the processing module 1201 is configured to construct a compensation vector for the time delay spectrum of at least some of the M symbols in the second data based on the phase difference, and to compensate the time delay spectrum of at least some of the M symbols in the second data based on the compensation vector.

[0375] That is, the phase compensation of the time delay spectrum of at least some of the M symbols in the second data based on the phase difference includes:

[0376] Based on the phase difference, a compensation vector is constructed for the time delay spectrum of at least some of the M symbols in the second data, and the time delay spectrum of at least some of the M symbols in the second data is compensated based on the compensation vector.

[0377] Optionally, the first data is a channel matrix in the time-frequency domain, and the dimension of the first data is N×M.

[0378] The aforementioned data processing device can improve sensing performance.

[0379] The data processing device provided in this application embodiment can achieve... Figure 6 The various processes implemented in the method embodiments achieve the same technical effect, and will not be described again here to avoid repetition.

[0380] like Figure 13 As shown, this application embodiment also provides a communication device 1300, including a processor 1301 and a memory 1302. The memory 1302 stores a program or instructions that can run on the processor 1301. For example, when the communication device 1300 is a first device, when the program or instructions are executed by the processor 1301, they implement the various steps of the above-described data processing method embodiment and can achieve the same technical effect. To avoid repetition, it will not be described again here.

[0381] This application embodiment also provides a device, including a processor and a communication interface, wherein the communication interface is coupled to the processor, and the processor is used to run programs or instructions to implement, as shown in the example. Figure 6 The steps in the method embodiment shown are illustrated. This device embodiment corresponds to the above method embodiment, and all implementation processes and methods of the above method embodiment can be applied to this device embodiment and achieve the same technical effect. The device can be... Figure 12 The data processing device shown. Specifically, Figure 14 A schematic diagram of the hardware structure of a device to implement an embodiment of this application.

[0382] The device 1400 includes, but is not limited to, at least some of the following components: radio frequency unit 1401, network module 1402, audio output unit 1403, input unit 1404, sensor 1405, display unit 1406, user input unit 1407, interface unit 1408, memory 1409, and processor 1410.

[0383] Those skilled in the art will understand that the device 1400 may also include a power supply (such as a battery) for supplying power to various components. The power supply may be logically connected to the processor 1410 through a power management system, thereby enabling functions such as managing charging, discharging, and power consumption through the power management system. Figure 14 The device structure shown does not constitute a limitation on the device. The device may include more or fewer components than shown, or combine certain components, or have different component arrangements, which will not be elaborated here.

[0384] It should be understood that, in this embodiment, the input unit 1404 may include a graphics processor 14041 and a microphone 14042. The graphics processor 14041 processes image data of still images or videos obtained by an image capture device (such as a camera) in video capture mode or image capture mode. The display unit 1406 may include a display panel 14061, which may be configured in the form of a liquid crystal display, an organic light-emitting diode, or the like. The user input unit 1407 includes at least one of a touch panel 14071 and other input devices 14072. The touch panel 14071 is also called a touch screen. The touch panel 14071 may include a touch detection device and a touch controller. Other input devices 14072 may include, but are not limited to, physical keyboards, function keys (such as volume control buttons, power buttons, etc.), trackballs, mice, and joysticks, which will not be described in detail here.

[0385] In this embodiment, after receiving downlink data from the network-side device, the radio frequency unit 1401 can transmit it to the processor 1410 for processing; in addition, the radio frequency unit 1401 can send uplink data to the network-side device. Typically, the radio frequency unit 1401 includes, but is not limited to, antennas, amplifiers, transceivers, couplers, low-noise amplifiers, duplexers, etc.

[0386] The memory 1409 can be used to store software programs or instructions, as well as various data. The memory 1409 may primarily include a first storage area for storing programs or instructions and a second storage area for storing data. The first storage area may store the operating system, application programs or instructions required for at least one function (such as sound playback, image playback, etc.). Furthermore, the memory 1409 may include volatile memory or non-volatile memory. The non-volatile memory may be read-only memory (ROM), programmable read-only memory (PROM), erasable programmable read-only memory (EPROM), electrically erasable programmable read-only memory (EEPROM), or flash memory. Volatile memory can be random access memory (RAM), static random access memory (SRAM), dynamic random access memory (DRAM), synchronous dynamic random access memory (SDRAM), double data rate synchronous dynamic random access memory (DDRSDRAM), enhanced synchronous dynamic random access memory (ESDRAM), synchronous link dynamic random access memory (SLDRAM), and direct memory bus RAM (DRRAM). The memory 1409 in this embodiment includes, but is not limited to, these and any other suitable types of memory.

[0387] Processor 1410 may include one or more processing units; optionally, processor 1410 integrates an application processor and a modem processor, wherein the application processor mainly handles operations involving the operating system, user interface, and applications, and the modem processor mainly handles wireless communication signals, such as a baseband processor. It is understood that the aforementioned modem processor may also not be integrated into processor 1410.

[0388] The processor 1410 is configured to perform a first processing on the first data to obtain second data, wherein the first data is data corresponding to the sensing signal, and the first processing is configured to align the time delay spectrum of M symbols in the first data, wherein the M symbols are the M symbols occupied by the sensing signal, and M is an integer greater than 1; and to perform a second processing on the second data to obtain third data, wherein the second processing is configured to perform phase compensation on the time delay spectrum of at least some of the M symbols in the second data.

[0389] Optionally, the first process includes:

[0390] Perform an inverse discrete Fourier transform (IDFT) on the first data at point P to obtain the time delay spectrum of the M symbols in the first data, where P is an integer greater than N and N is the number of subcarriers occupied by the sensing signal.

[0391] The time delay spectra of the M symbols in the first data are aligned.

[0392] Optionally, the alignment process for the time delay spectra of the M symbols in the first data includes:

[0393] Obtain the shift information between the time delay spectra of the M symbols in the first data;

[0394] The time delay spectrum of at least some of the M symbols in the first data is reverse cyclically shifted according to the shift information, and the reverse cyclic shift is used to align the time delay spectrum of the M symbols in the first data.

[0395] Optionally, obtaining the shift information between the time delay spectra of the M symbols in the first data includes the following:

[0396] The shift information between the time delay spectra of the M symbols in the first data is obtained by means of a reference path.

[0397] The shift information between the delay spectra of the M symbols in the first data is obtained by using a group delay method.

[0398] Optionally, obtaining the shift information between the time delay spectra of the M symbols in the first data via a reference path includes:

[0399] Obtain the cell index of the reference path in the time delay spectrum of the M symbols in the first data, and calculate the shift information based on the cell index. The shift information includes the difference between the cell indices corresponding to the M symbols, or the shift information includes the difference between the cell index corresponding to the M-1 symbols and the cell index corresponding to the first symbol.

[0400] Optionally, obtaining the shift information between the delay spectra of the M symbols in the first data through a group delay method includes:

[0401] Based on the time delay spectra of the M symbols in the first data, the correlation spectrum between the second symbol and the first symbol is calculated, and the shift information includes the cell index corresponding to the maximum amplitude value in the correlation spectrum between the second symbol and the first symbol; or

[0402] Based on the time delay spectrum of the M symbols in the first data, the correlation spectrum of M-1 symbols with the first symbol is calculated respectively, and the shift information includes the cell index corresponding to the maximum amplitude value in the correlation spectrum of the M-1 symbols with the first symbol respectively;

[0403] Wherein, the first symbol is one of the M symbols, the M-1 symbols are the M-1 symbols other than the first symbol among the M symbols, and the second symbol is one of the M symbols other than the first symbol.

[0404] Optionally, the correlation spectrum includes:

[0405] For r j and r k The first correlation spectrum obtained by performing cyclic cross-correlation, or the correlation spectrum obtained by |r j |and|r k The second correlation spectrum obtained by performing cyclic cross-correlation operation, wherein the r j and r k Represent the time delay spectra of two symbols out of the M symbols in the first data, |r j |and|r k | represents the amplitude value of the time delay spectrum of the two symbols respectively.

[0406] Optionally, the second data is the data obtained from the alignment process; or

[0407] The first process further includes:

[0408] The aligned data is downsampled by a factor of P / N along the time delay dimension, and the second data is the data obtained after the downsampling.

[0409] Optionally, P equals α × N, where α is an integer obtained based on a first table, the first table including at least one index and at least one value of α;

[0410] Alternatively, P can be an integer obtained based on a second table, which includes at least one index and at least one value of P.

[0411] Optionally, the second process includes:

[0412] Obtain the phase difference between the time delay spectra of the M symbols in the second data;

[0413] Phase compensation is performed on the time delay spectrum of at least some of the M symbols in the second data based on the phase difference.

[0414] Optionally, obtaining the phase difference between the time delay spectra of the M symbols in the second data includes the following:

[0415] The phase difference between the time delay spectra of the M symbols in the second data is obtained by means of a reference path.

[0416] The phase difference between the time delay spectra of the M symbols in the second data is obtained by phase construction method;

[0417] The phase difference between the time delay spectra of the M symbols in the second data is obtained by the group phase difference method.

[0418] Optionally, obtaining the phase difference between the time delay spectra of the M symbols in the second data via a reference path includes:

[0419] Obtain the phase of the unit corresponding to the reference path in the time delay spectrum of the M symbols in the second data, and calculate the phase difference between the time delay spectra of the M symbols in the second data based on the phase. The phase difference includes the difference between the phases corresponding to the M symbols, or the phase difference includes the difference between the phases corresponding to the M-1 symbols and the phase corresponding to the first symbol, where the first symbol is one of the M symbols and the M-1 symbols are the M-1 symbols other than the first symbol.

[0420] Optionally, the unit corresponding to the reference path in the time delay spectrum of the M symbols in the second data includes one of the following:

[0421] The cell in the second data where the reference path is located on the time delay spectrum of the M symbols;

[0422] The cell corresponding to the mean of the cell index set;

[0423] The cell corresponding to the cell index that appears most frequently in the cell index set;

[0424] The cell index set includes the cell indices of the reference path in the second data on the time delay spectrum of the M symbols.

[0425] Optionally, obtaining the phase difference between the time delay spectra of the M symbols in the second data through phase construction includes:

[0426] The phase difference between the time delay spectra of the M symbols in the second data is constructed based on the shift information, wherein the shift information is the shift information between the time delay spectra of the M symbols in the first data.

[0427] Optionally, the phase difference between the time delay spectra of the M symbols in the second data obtained by the group phase difference method includes:

[0428] The phase difference of the time delay spectrum between the j-th and k-th symbols among the M symbols in the second data. j is less than or equal to M, and k is less than or equal to M;

[0429] Wherein, the phase difference Includes the following:

[0430] The average of the phase differences between multiple units, wherein the phase differences between multiple units are the phase differences between multiple units in the time delay spectrum of the second data in the j-th and k-th symbols;

[0431] The phase value of the element whose index equals the shift information in the first correlation spectrum, wherein the shift information is the shift information of the first data between the time delay spectra of the j-th and k-th symbols, and the first correlation spectrum is the phase value of the element whose index equals the shift information in the first correlation spectrum. j and r k The correlation spectrum obtained by performing cyclic cross-correlation operation, wherein r j and r k These represent the time delay spectra of the j-th and k-th symbols of the first data in the M symbols, respectively;

[0432] The phase value of the element whose index is equal to the first value in the third correlation spectrum, wherein the third correlation spectrum is the correlation spectrum obtained by performing a cyclic cross-correlation operation on the time delay spectra of the second data at the j-th symbol and the k-th symbol.

[0433] Optionally, the step of performing phase compensation on the time delay spectrum of at least some of the M symbols in the second data based on the phase difference includes:

[0434] Based on the phase difference, a compensation vector is constructed for the time delay spectrum of at least some of the M symbols in the second data, and the time delay spectrum of at least some of the M symbols in the second data is compensated based on the compensation vector.

[0435] Optionally, the first data is a channel matrix in the time-frequency domain, and the dimension of the first data is N×M.

[0436] The aforementioned equipment can improve sensing performance.

[0437] It is understood that the implementation process of each implementation method mentioned in this embodiment can refer to the relevant description of the data processing method embodiment and achieve the same or corresponding technical effects. To avoid repetition, it will not be described again here.

[0438] It should be noted that this embodiment uses the first device as the terminal for illustration. In this application embodiment, the first device can also be a network-side device, that is, the aforementioned network-side device can also be implemented. Figure 6The steps in the method shown.

[0439] This application also provides a readable storage medium storing a program or instructions. When the program or instructions are executed by a processor, they implement the various processes of the above-described data processing method embodiments and achieve the same technical effects. To avoid repetition, they will not be described again here.

[0440] The processor mentioned above is the processor in the terminal described in the above embodiments. The readable storage medium includes computer-readable storage media, such as computer read-only memory (ROM), random access memory (RAM), magnetic disk, or optical disk. In some examples, the readable storage medium may be a non-transient readable storage medium.

[0441] This application embodiment also provides a chip, which includes a processor and a communication interface. The communication interface is coupled to the processor. The processor is used to run programs or instructions to implement the various processes of the above data processing method embodiments and can achieve the same technical effect. To avoid repetition, it will not be described again here.

[0442] It should be understood that the chip mentioned in the embodiments of this application may also be referred to as a system-on-a-chip, system chip, chip system, or system-on-a-chip, etc.

[0443] This application also provides a computer program / program product, which is stored in a storage medium and executed by at least one processor to implement the various processes of the above-described data processing method embodiments, and can achieve the same technical effect. To avoid repetition, it will not be described again here.

[0444] It should be noted that, in this document, the terms "comprising," "including," or any other variations thereof are intended to cover non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements includes not only those elements but also other elements not expressly listed, or elements inherent to such a process, method, article, or apparatus. Without further limitations, an element defined by the phrase "comprising one..." does not exclude the presence of other identical elements in the process, method, article, or apparatus that includes that element. Furthermore, it should be noted that the scope of the methods and apparatuses in the embodiments of this application is not limited to performing functions in the order shown or discussed, but may also include performing functions substantially simultaneously or in the reverse order, depending on the functions involved. For example, the described methods may be performed in a different order than described, and various steps may be added, omitted, or combined. Additionally, features described with reference to certain examples may be combined in other examples.

[0445] From the above description of the embodiments, those skilled in the art can clearly understand that the methods of the above embodiments can be implemented by means of computer software products plus necessary general-purpose hardware platforms, and of course, they can also be implemented by hardware. The computer software product is stored in a storage medium (such as ROM, RAM, magnetic disk, optical disk, etc.) and includes several instructions to cause the terminal or network-side device to execute the methods described in the various embodiments of this application.

[0446] The embodiments of this application have been described above with reference to the accompanying drawings. However, this application is not limited to the specific embodiments described above. The specific embodiments described above are merely illustrative and not restrictive. Those skilled in the art can make many other implementations under the guidance of this application without departing from the spirit and scope of the claims. All of these implementations are within the protection scope of this application.

Claims

1. A data processing method, characterized by, The method comprises: A first device performs first processing on first data to obtain second data, wherein the first data is data corresponding to a sensing signal, and the first processing is used for aligning time delay spectrums of M symbols in the first data, the M symbols are M symbols occupied by the sensing signal, and M is an integer greater than 1. The first device performs second processing on the second data to obtain third data, wherein the second processing is used for phase compensation on time delay spectrums of at least part of the M symbols in the second data.

2. The method of claim 1, wherein, The first processing comprises: performing inverse discrete Fourier transform (IDFT) on the first data to obtain time delay spectrums of the M symbols in the first data, wherein P is an integer greater than N, and N is the number of subcarriers occupied by the sensing signal; aligning the time delay spectrums of the M symbols in the first data.

3. The method of claim 2, wherein, The aligning of the time delay spectrums of the M symbols in the first data comprises: obtaining shift information between the time delay spectrums of the M symbols in the first data; and performing reverse cyclic shift on the time delay spectrums of at least part of the M symbols in the first data according to the shift information, so as to align the time delay spectrums of the M symbols in the first data.

4. The method of claim 3, wherein, The obtaining of the shift information between the time delay spectrums of the M symbols in the first data comprises one of the following: the shift information between the time delay spectrums of the M symbols in the first data is obtained by reference diameter; and the shift information between the time delay spectrums of the M symbols in the first data is obtained by group delay.

5. The method of claim 4, wherein, The obtaining of the shift information between the time delay spectrums of the M symbols in the first data by reference diameter comprises: obtaining unit indexes of reference diameters on the time delay spectrums of the M symbols in the first data, and calculating the shift information based on the unit indexes, wherein the shift information comprises a difference value between the unit indexes corresponding to the M symbols, or the shift information comprises a difference value between the unit index corresponding to a first symbol and the unit indexes corresponding to M-1 symbols.

6. The method of claim 4, wherein, The obtaining of the shift information between the time delay spectrums of the M symbols in the first data by group delay comprises: calculating a correlation spectrum of a second symbol and a first symbol based on the time delay spectrums of the M symbols in the first data, wherein the shift information comprises a unit index corresponding to a maximum amplitude value in the correlation spectrum of the second symbol and the first symbol; or calculating correlation spectrums of M-1 symbols and the first symbol respectively based on the time delay spectrums of the M symbols in the first data, wherein the shift information comprises unit indexes corresponding to maximum amplitude values in the correlation spectrums of the M-1 symbols and the first symbol respectively; wherein the first symbol is one of the M symbols, the M-1 symbols are M-1 symbols other than the first symbol among the M symbols, and the second symbol is one symbol other than the first symbol among the M symbols.

7. The method of claim 6, wherein, The correlation spectrum comprises: A first correlation spectrum obtained by performing a cyclic cross-correlation operation on rj and rk, or a second correlation spectrum obtained by performing a cyclic cross-correlation operation on |rj| and |rk| j and r k respectively represent time delay spectra of two symbols in the M symbols in the first data, and |rj| and |rk| respectively represent amplitude values of the time delay spectra of the two symbols.

8. The method according to any one of claims 2 to 7, characterized in that, the second data is data obtained by the aligning; or the first processing further comprises: The P / N times down-sampling is performed on the aligned data along the delay dimension, and the second data is obtained after the down-sampling.

9. The method according to any one of claims 2 to 7, characterized in that, The P is equal to α×N, wherein the α is an integer obtained based on a first table, and the first table includes at least one index and at least one value of the α. Alternatively, the P is an integer obtained based on a second table, and the second table includes at least one index and at least one value of the P.

10. The method according to any one of claims 1 to 9, characterized in that, The second processing includes: obtaining a phase difference between the delay profiles of the M symbols in the second data; performing phase compensation on the delay profiles of at least part of the M symbols in the second data according to the phase difference.

11. The method of claim 10, wherein, The obtaining of the phase difference between the delay profiles of the M symbols in the second data includes one of: obtaining the phase difference between the delay profiles of the M symbols in the second data by a reference diameter method; obtaining the phase difference between the delay profiles of the M symbols in the second data by a phase construction method; obtaining the phase difference between the delay profiles of the M symbols in the second data by a group phase difference method.

12. The method of claim 11, wherein, The obtaining of the phase difference between the delay profiles of the M symbols in the second data by the reference diameter method includes: obtaining a phase of a unit corresponding to a reference diameter in the delay profile of the M symbols in the second data, and calculating the phase difference between the delay profiles of the M symbols in the second data based on the phase, wherein the phase difference includes a difference between the phases corresponding to the M symbols, or the phase difference includes a difference between a phase corresponding to a first symbol and phases corresponding to M-1 symbols, the first symbol being one of the M symbols, and the M-1 symbols being M-1 symbols other than the first symbol.

13. The method of claim 12, wherein, The unit corresponding to the reference diameter in the delay profile of the M symbols in the second data includes one of: a unit where the reference diameter is located in the delay profile of the M symbols in the second data; a unit corresponding to a mean value of a unit index set; a unit corresponding to a unit index that appears most frequently in the unit index set; wherein the unit index set includes unit indexes of the unit corresponding to the reference diameter in the delay profile of the M symbols in the second data.

14. The method of claim 11, wherein, The obtaining of the phase difference between the delay profiles of the M symbols in the second data by the phase construction method includes: constructing the phase difference between the delay profiles of the M symbols in the second data based on shift information, the shift information being shift information between the delay profiles of the M symbols in the first data.

15. The method of claim 11, wherein, The phase difference between the delay profiles of the M symbols in the second data obtained by the group phase difference method includes: a phase difference of a time delay spectrum of a jth symbol and a kth symbol in the M symbols in the second data j is less than or equal to M, and k is less than or equal to M wherein the phase difference comprises one of the following: a mean value of phase differences between a plurality of units, the phase differences between the plurality of units being phase differences between a plurality of units in the delay profile of the jth symbol and the kth symbol in the second data; a phase value of an element in the first correlation spectrum with an index equal to the shift information, wherein the shift information is shift information between a time delay spectrum of the first data in the jth symbol and a time delay spectrum of the first data in the kth symbol, and the first correlation spectrum is a correlation spectrum obtained by performing a cyclic cross-correlation operation on r j and r k , respectively, represent a time delay spectrum of the first data in the jth symbol and a time delay spectrum of the first data in the kth symbol in the M symbols, respectively. j and r k , respectively, represent a time delay spectrum of the first data in the jth symbol and a time delay spectrum of the first data in the kth symbol in the M symbols, respectively. a phase value of an element with an index equal to a first value in a third correlation spectrum, wherein the third correlation spectrum is a correlation spectrum obtained by performing a cyclic cross-correlation operation on the delay profile of the jth symbol and the kth symbol in the second data.

16. The method according to any one of claims 10 to 15, characterized in that, The phase compensating of the time delay spectrum of at least part of the M symbols in the second data according to the phase difference comprises: constructing a compensation vector of the time delay spectrum of at least part of the M symbols in the second data according to the phase difference, and compensating the time delay spectrum of at least part of the M symbols in the second data based on the compensation vector.

17. The method of any one of claims 1 to 16, wherein, The first data is a channel matrix in a time-frequency domain, and the dimension of the first data is N x M.

18. A data processing apparatus, characterized by comprise: a processing module, configured to perform first processing on first data to obtain second data, wherein the first data is data corresponding to a sensing signal, and the first processing is used for aligning time delay spectrums of M symbols in the first data, the M symbols being M symbols occupied by the sensing signal, and M being an integer greater than 1; The processing module is further configured to perform second processing on the second data to obtain third data, and the second processing is used for phase compensating the time delay spectrums of at least part of the M symbols in the second data.

19. The apparatus of claim 18, wherein, The processing module is configured to perform P-point inverse discrete Fourier transform (IDFT) on the first data to obtain the time delay spectrums of the M symbols in the first data, P being an integer greater than N, and N being a number of subcarriers occupied by the sensing signal; and perform alignment processing on the time delay spectrums of the M symbols in the first data.

20. The apparatus of claim 19, wherein, The processing module is configured to perform P-point IDFT on the first data to obtain the time delay spectrums of the M symbols in the first data, P being an integer greater than N, and N being a number of subcarriers occupied by the sensing signal; and obtain shift information between the time delay spectrums of the M symbols in the first data; and perform reverse cyclic shift on the time delay spectrums of at least part of the M symbols in the first data according to the shift information, the reverse cyclic shift being used for aligning the time delay spectrums of the M symbols in the first data.

21. The apparatus of claim 20, wherein, The processing module is configured to obtain the shift information between the time delay spectrums of the M symbols in the first data in a reference radius manner; or The processing module is configured to obtain the shift information between the time delay spectrums of the M symbols in the first data in a group time delay manner.

22. The apparatus of any one of claims 19-21, wherein, The second data is data obtained through the alignment processing; or The processing module is further configured to perform P / N times downsampling on the data after the alignment processing along a time delay dimension, and the second data is data obtained after the downsampling.

23. The apparatus of any one of claims 18-22, wherein, The processing module is configured to obtain a phase difference between the time delay spectrums of the M symbols in the second data; and perform phase compensating on the time delay spectrums of at least part of the M symbols in the second data according to the phase difference.

24. The apparatus of claim 23, wherein, The processing module is configured to obtain the phase difference between the time delay spectrums of the M symbols in the second data in a reference radius manner; or The processing module is configured to obtain the phase difference between the time delay spectrums of the M symbols in the second data in a phase construction manner; or The processing module is configured to obtain the phase difference between the time delay spectrums of the M symbols in the second data in a group phase difference manner.

25. An apparatus comprising: A computer program product stored in a storage medium, the computer program product being executed by at least one processor to implement the steps of the data processing method according to any one of claims 1 to 17.

26. A readable storage medium characterized by, A computer program product stored in a storage medium, the computer program product being executed by at least one processor to implement the steps of the data processing method according to any one of claims 1 to 17.

27. A computer program product, characterised in that, A computer program product stored in a storage medium, the computer program product being executed by at least one processor to implement the steps of the data processing method according to any one of claims 1 to 17.

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