Radio frequency channel adaptive measurement and control method and related device

Abstract

The invention relates to a radio frequency channel adaptive measurement and control method and a related device. The method comprises the following steps: synchronously acquiring digital baseband input, radio frequency feedback output and an instantaneous power supply voltage signal; constructing a three-dimensional nonlinear distortion model which describes the output of the power amplifier as an input characteristic and power supply fluctuation joint function; calculating a compensation parameter varying with the voltage based on the model to implement dynamic pre-distortion; the signal peak value is adjusted by calculating the cross correlation coefficient of the radio frequency residual error and the power supply voltage, and the direct-current power supply voltage is dynamically reconstructed according to the throughput index. According to the invention, through three-dimensional modeling decoupling device and power supply characteristics, accurate linearization compensation is realized under unsteady state power supply, hardware transient response requirements are reduced, and communication quality and energy efficiency are balanced in a self-adaptive manner.

Description

Technical Field

[0001] This application relates to the field of satellite communications, and in particular to a radio frequency channel adaptive measurement and control method and related apparatus. Background Technology

[0002] In modern high-speed data transmission terminals and satellite communication systems, to improve data transmission rates under limited spectrum resources, communication protocols generally employ wideband complex modulation signals with high peak-to-average power ratios (PAPR). As a core component of the radio frequency (RF) front-end, the linearity of the power amplifier directly determines the signal quality of the communication link. To improve energy efficiency while maintaining linearity, the industry widely adopts digital predistortion technology. This involves preprocessing the input signal in the digital baseband domain to generate distortion components opposite to the nonlinear characteristics of the power amplifier, thereby canceling the nonlinear products at the power amplifier's output.

[0003] Existing digital predistortion measurement and modeling methods are typically based on an idealized assumption: that the power amplifier's power supply is a constant DC source, or that voltage fluctuations are negligible relative to changes in the RF signal. Based on this assumption, traditional predistortion models primarily construct a two-dimensional mapping between the digital baseband input signal and the RF feedback output signal. However, in real-world high-speed broadband communication scenarios, when the modulation signal has a wide instantaneous bandwidth and high peak power, the power amplifier generates significant transient current extraction requirements. Due to limitations in size, cost, and the loop response bandwidth of the power management unit itself, commercially available power supplies typically struggle to maintain absolute voltage stability on a microsecond-scale timescale, resulting in voltage ripple or drops at the power amplifier's supply terminal that rapidly change with the signal envelope.

[0004] Unexpected power supply voltage fluctuations directly alter the quiescent operating point of the power amplifier, causing instantaneous drift in its gain and phase characteristics. In traditional two-dimensional modeling systems, this dynamic interference introduced by the physical power supply layer cannot be detected and can only be incorrectly attributed to model fitting residuals or random noise. When the power supply voltage drops, the saturation point of the power amplifier shifts downward, resulting in dynamic gain compression that existing models cannot predict. At this point, the predistortion parameters obtained solely from table lookups or polynomial calculations based on the input signal amplitude will no longer match the current physical conditions, leading to a significant decrease in the correction performance of the predistortion system, manifested as a deterioration in the adjacent channel power leakage ratio or an excessive error vector amplitude. Summary of the Invention

[0005] In order to compensate for power supply-induced distortion through signal processing without increasing expensive hardware costs, this application provides an adaptive measurement and control method and related apparatus for radio frequency channels.

[0006] Firstly, this application provides a radio frequency channel adaptive measurement and control method, which adopts the following technical solution: An adaptive measurement and control method for radio frequency channels includes the following steps: S1. During the operation of the data transmission terminal, three time-domain signals are acquired synchronously; wherein, the three time-domain signals include the digital baseband input signal X, the radio frequency feedback output signal Y after down-conversion and synchronous processing, and the instantaneous power supply voltage signal V at the power amplifier power supply terminal; S2. Construct a three-dimensional nonlinear distortion model based on the three time-domain signals, wherein the three-dimensional nonlinear distortion model describes the output of the power amplifier as a joint function of the input signal characteristics and the power supply voltage fluctuation; S3. Based on the three-dimensional nonlinear distortion model, calculate the predistortion compensation parameters that dynamically change with the instantaneous power supply voltage signal V, and use the predistortion compensation parameters to perform real-time predistortion processing on the digital baseband input signal X to generate an RF drive signal and send it to the power amplifier; S4. Perform hierarchical closed-loop feedback optimization, adjust the peak characteristics of the digital baseband input signal X by calculating the cross-correlation coefficient between the RF output residual signal and the instantaneous power supply voltage signal V, and dynamically reconstruct the DC power supply voltage of the power amplifier power supply terminal according to the data transmission capability of the data transmission terminal; wherein, the RF output residual signal is determined based on the difference between the digital baseband input signal X and the RF feedback output signal Y.

[0007] By adopting the above technical solution, this application describes the output of the power amplifier as a joint function of the input signal characteristics and the power supply voltage fluctuation, thereby achieving effective decoupling of the inherent nonlinear characteristics of the power amplifier and the power supply ripple sensitivity characteristics at the physical modeling level. This joint functional relationship can quantify the independent influence components of voltage fluctuations on the RF output, preventing the predistortion algorithm from misjudging the transient gain compression caused by power supply voltage drops as device time drift or model fitting error, and ensuring the accuracy and convergence stability of the nonlinear distortion model under unsteady power supply environments.

[0008] A three-dimensional nonlinear distortion model is used to calculate the predistortion compensation parameters that dynamically change with voltage, and real-time predistortion processing is performed on the digital baseband input signal to generate an RF drive signal with inverse compensation characteristics in the digital domain. This processing logic utilizes the microsecond-level response speed of digital signal processing to pre-compensate the power amplifier gain loss caused by power supply voltage drops in the analog domain. This allows the data transmission terminal to maintain the linearity of the RF link through active compensation in the digital domain without requiring expensive power supply hardware with high transient response, significantly reducing the transient current design margin requirements of the hardware system.

[0009] A hierarchical closed-loop feedback optimization was implemented. By calculating the cross-correlation coefficient between the RF output residual signal and the instantaneous power supply voltage signal, a statistical criterion was established to distinguish between power supply-induced distortion and model residual distortion. Based on this cross-correlation coefficient, the peak characteristics of the digital baseband input signal were adjusted, enabling a targeted reduction in the signal peak-to-average power ratio (PAPR) only when the power supply capability became a linearity bottleneck. This alleviated the instantaneous load pressure on the power supply while avoiding the indiscriminate damage to signal waveform fidelity caused by fixed-threshold peak clipping. Furthermore, the DC power supply voltage at the power amplifier's power supply end was dynamically reconstructed according to the data transmission capability, establishing a linkage mechanism between service throughput and physical power supply capability. When the digital peak clipping strategy could not meet the linearity requirements, resulting in limited throughput, the dynamic range of the power amplifier was extended by physically increasing the voltage reference value, achieving an adaptive balance between communication quality, data rate, and hardware power consumption.

[0010] Optionally, step S2 includes the following sub-steps: S21. Extract the static mapping relationship between the digital baseband input signal X and the radio frequency feedback output signal Y, and construct a static nonlinear term characterizing the inherent distortion characteristics of the power amplifier under the reference rated voltage; wherein, the reference rated voltage is the nominal DC voltage value of the power supply of the power amplifier; S22. Extract the fluctuation characteristics of the instantaneous power supply voltage signal V, and construct a dynamic power supply modulation term that characterizes the sensitivity of the power amplifier's nonlinear characteristics as the fluctuation of the instantaneous power supply voltage signal V changes; S23. The dynamic power supply modulation term is superimposed on the static nonlinear term as a time-varying weighting coefficient to generate the three-dimensional nonlinear distortion model, such that the output response of the three-dimensional nonlinear distortion model includes dynamic gain compression prediction generated by the drop of the instantaneous power supply voltage signal V.

[0011] By employing the above technical solution, a static nonlinear term is constructed by extracting the static mapping relationship between the digital baseband input signal and the RF feedback output signal under the reference rated voltage. This establishes the inherent distortion reference of the power amplifier when it is unaffected by power supply fluctuations, providing a physical reference coordinate for distinguishing device characteristics from power environment characteristics. The fluctuation characteristics of the instantaneous power supply voltage signal are extracted to construct a dynamic power supply modulation term, which is then superimposed on the static nonlinear term as a time-varying weighting coefficient, thereby generating a three-dimensional nonlinear distortion model. This modeling method quantifies the instantaneous voltage drop physical quantity as a dynamic correction factor for the static model, achieving orthogonal decoupling between the inherent nonlinearity of the power amplifier and the power supply modulation nonlinearity in its mathematical structure. This enables the model to output dynamic gain compression predictions in real time based on the instantaneous voltage state, preventing model parameter divergence caused by confusing static and dynamic distortions in unsteady power supply environments. It ensures that the system can independently digitally compensate for specific nonlinear components caused by voltage drops.

[0012] Optionally, step S3 includes the following sub-steps: S31. Monitor the instantaneous power supply voltage signal V in real time, and calculate the pre-distortion compensation parameter corresponding to the voltage drop amplitude of the instantaneous power supply voltage signal V relative to the reference rated voltage, based on the voltage sensitivity relationship established in the three-dimensional nonlinear distortion model. S32. Generate an amplitude correction factor that corresponds inversely to the voltage drop amplitude based on the pre-distortion compensation parameters; S33. The amplitude correction factor is applied to the digital baseband input signal X to generate the RF drive signal with pre-amplified amplitude to offset the power amplifier gain loss caused by the drop in the instantaneous power supply voltage signal V.

[0013] By employing the above technical solution, the voltage sensitivity relationship established in the three-dimensional nonlinear distortion model is used to map the sag of the instantaneous power supply voltage signal relative to the reference rated voltage as a pre-distortion compensation parameter. An amplitude correction factor, inversely corresponding to this sag, is then generated in the digital domain. This amplitude correction factor is directly applied to the digital baseband input signal, pre-amplifying its amplitude before the signal enters the digital-to-analog conversion. The fast response characteristics of digital signal processing are used to precisely align and cancel the power supply voltage sag on the time axis. This mechanism can physically force the power amplifier's output gain to remain stable, effectively overcoming the physical bottleneck of traditional power management units, which are unable to compensate for rapid voltage fluctuations in real time due to limited transient response bandwidth. This ensures that the energy envelope of the RF drive signal can dynamically adapt to instantaneous changes in power supply capability.

[0014] Optionally, step S4 includes the following sub-steps: S41. Obtain the radio frequency output residual signal after pre-distortion processing, and calculate the cross-correlation coefficient between the radio frequency output residual signal and the instantaneous power supply voltage signal V; S42. Compare the cross-correlation coefficient with a preset correlation threshold. If the cross-correlation coefficient is greater than the correlation threshold, it is determined that the current distortion is mainly caused by insufficient power supply capacity, and the peak clipping control strategy is adjusted to reduce the peak-to-average power ratio of the digital baseband input signal X until the cross-correlation coefficient drops below the correlation threshold. S43. After implementing the adjustment of the peak-shaving control strategy, monitor the effective data throughput index of the data transmission terminal in real time; S44. If the effective data throughput indicator is lower than the preset service compliance line, a hardware control command is generated and sent to the power management unit of the data transmission terminal to control the power management unit to increase the DC voltage reference value applied to the power amplifier power supply terminal, and after the DC voltage reference value is increased, the peak clipping control strategy is restored to the initial state; wherein, the initial default value of the DC voltage reference value is equal to the reference rated voltage.

[0015] By employing the aforementioned technical solution, a statistical criterion is established to quantify the contribution of power supply fluctuations to nonlinear distortion by calculating the cross-correlation coefficient between the RF output residual signal and the instantaneous power supply voltage signal. This logically decouples the dominant distortion caused by insufficient power supply capacity from the residual distortion caused by model fitting errors. Based on this criterion, the peak-to-average power ratio (PAPR) is adjusted, ensuring that the operation is only intervened to reduce the PAPR when the power supply becomes a linearity bottleneck, avoiding ineffective compression of the signal dynamic range when the power supply capacity is sufficient. Furthermore, the effective data throughput index is compared with the service performance target, and the power management unit is controlled to increase the DC voltage reference value when the throughput is limited. This constructs a complete closed loop from physical layer signal quality to application layer service performance and then to hardware layer power supply capacity, ensuring that the system can dynamically expand the physical linear operating range of the power amplifier according to actual data transmission needs, achieving optimal energy efficiency configuration while ensuring communication speed.

[0016] Optionally, step S42 includes the following sub-steps: S421. Call the dynamic power supply modulation term in the three-dimensional nonlinear distortion model to calculate the dynamic saturation input boundary allowed for the power amplifier to maintain linear operation under the fluctuation state of the current instantaneous power supply voltage signal V. S422. Configure the dynamic saturation input boundary as a time-varying threshold for the peak-shaving control strategy; S423. The digital baseband input signal X is judged point by point using the time-varying threshold, and amplitude compression is performed only on signal sampling points whose amplitude exceeds the dynamic saturation input boundary, thereby reducing the peak-to-average power ratio while maximizing the preservation of the waveform characteristics of the digital baseband input signal X that does not exceed the dynamic saturation input boundary; S424. Recalculate the cross-correlation coefficient between the RF output residual signal and the instantaneous power supply voltage signal V. If the recalculated cross-correlation coefficient is still greater than the correlation threshold, repeat S421 to S423 based on the updated fluctuation state of the instantaneous power supply voltage signal V until the cross-correlation coefficient drops below the correlation threshold.

[0017] By employing the aforementioned technical solution, the dynamic power modulation term in the three-dimensional nonlinear distortion model is invoked to calculate the dynamic saturation input boundary allowed for the power amplifier to maintain linear operation under the current instantaneous power supply voltage fluctuation state. This boundary is then transformed into a time-varying threshold that fluctuates with voltage and configured for the peak clipping control strategy. This time-varying threshold is used to perform point-by-point discrimination and compression of the digital baseband input signal, ensuring that peak clipping is strictly limited to signal sampling points exceeding the physical instantaneous linearity capability. This dynamic clipping mechanism based on physical boundaries effectively reduces the peak-to-average power ratio (PAPR) to eliminate cross-correlation alarms while maximizing the preservation of waveform characteristics within the linear bearing range of the power supply voltage. It avoids the indiscriminate degradation of the signal error vector amplitude across all time periods caused by traditional fixed-threshold peak clipping, significantly improving the signal demodulation quality under unsteady power supply environments.

[0018] Optionally, S44 includes the following sub-steps: S441. Based on the static nonlinear term in the three-dimensional nonlinear distortion model, determine the theoretical saturated output power of the power amplifier at the preset linearity target value; S442. Combining the dynamic gain compression prediction output by the three-dimensional nonlinear distortion model, calculate the current power backoff value caused by the drop in the instantaneous power supply voltage signal V, and use the voltage sensitivity relationship to reverse map the power backoff value into a voltage compensation increment. S443. The voltage compensation increment is superimposed on the current DC voltage reference value to generate the hardware control command, so that the improved hardware power supply voltage compensation is affected by the linearity loss characterized by the dynamic gain compression prediction. S444. After detecting that the power management unit has executed the hardware control instruction, reset the time-varying threshold in the peak clipping control strategy to the initial default value.

[0019] By adopting the above technical solution, the theoretical saturated output power under the preset linearity target value is determined based on the static nonlinear term. Combined with dynamic gain compression prediction, the specific power regression value caused by voltage drop is calculated. The voltage sensitivity relationship is used to accurately reverse-map this physical power loss into a voltage compensation increment. This increment is superimposed on the DC voltage reference value to generate hardware control commands, ensuring that the boosted hardware supply voltage accurately fills the linearity gap represented by dynamic gain compression at the physical energy level. Upon detecting the execution of the voltage boost command, the time-varying threshold in the peak-shaving control strategy is reset, promptly releasing the digital domain's limitation on the signal dynamic range. Thus, after the physical power supply capability is enhanced at the hardware level, a high-fidelity signal transmission mode is immediately restored, achieving seamless switching and coordination between hardware resource investment and software signal processing strategies.

[0020] Secondly, the computer device provided in this application adopts the following technical solution: A computer device comprising: One or more processors; Memory; One or more applications, wherein the one or more applications are stored in the memory and configured to be executed by the one or more processors, the one or more applications being configured to: The above-described adaptive measurement and control method for the radio frequency channel is implemented.

[0021] Thirdly, this application provides a computer-readable storage medium that adopts the following technical solution: A computer-readable storage medium storing a computer program that can be loaded by a processor and executed as described above.

[0022] The storage medium stores at least one instruction, at least one program, a code set, or an instruction set, wherein the at least one instruction, the at least one program, the code set, or the instruction set is loaded and executed by the processor to implement the following: Such as the adaptive measurement and control method for radio frequency channels mentioned above.

[0023] In summary, this application includes at least one of the following beneficial technical effects: 1. This application significantly reduces the reliance on power supply hardware transient response metrics, enabling high-performance broadband communication with low-cost hardware. It abandons the traditional approach of brute-force ripple suppression using expensive power supply chips, instead employing a side-channel approach to introduce power supply ripple as a known interference source into the three-dimensional nonlinear model. Through real-time digital compensation within the inner ring, even when faced with large current draws from high-speed broadband signals with high peak-to-average power ratios, ordinary commercial-grade power supplies can maintain highly linear RF output despite voltage drops. This eliminates the need for excessively designed power supply modules in data transmission terminals to meet extreme instantaneous peak power consumption, significantly reducing material costs and size.

[0024] 2. This invention solves the problem of traditional two-dimensional DPD models failing under unsteady power supply environments, improving measurement accuracy and link robustness under complex operating conditions. Existing technologies typically assume a constant PA supply voltage; once the voltage fluctuates, the predistortion model fails, leading to a surge in the bit error rate. This application constructs a three-dimensional joint function of the input signal, power supply voltage, and output signal, which can accurately distinguish between the nonlinear characteristics of the power amplifier itself and the dynamic gain compression caused by insufficient power supply. This decoupling mechanism ensures that even under harsh operating conditions such as insufficient battery power or severe power supply ripple, the DPD algorithm can still converge quickly and lock into the optimal operating point, avoiding communication interruptions caused by model mismatch.

[0025] 3. Through a unique hierarchical closed-loop feedback mechanism, the system can intelligently decide on the optimal compensation strategy: using cross-correlation coefficients, it only reduces the signal peak value through peak clipping when the power supply is insufficient, and uses dynamic saturation boundaries to preserve signal details to the greatest extent, avoiding the unnecessary sacrifice of throughput by traditional fixed threshold peak clipping; it only triggers hardware boost when the throughput is below standard, avoiding keeping the PA in an unnecessarily high voltage state for a long time to maintain linearity. This mechanism enables the terminal to adaptively find the operating state with the highest energy efficiency based on the service load and physical environment. Attached Figure Description

[0026] Figure 1 A flowchart illustrating an adaptive measurement and control method for a radio frequency channel in one embodiment of the present invention is shown. Detailed Implementation

[0027] The present application will be further described in detail below with reference to the accompanying drawings. It should be understood that the specific embodiments described herein are merely illustrative of the application and are not intended to limit the scope of the application.

[0028] In the following description, numerous specific details are set forth for purposes of explanation in order to provide a thorough understanding of the inventive concept. As part of this specification, some of the accompanying drawings of this disclosure are block diagrams illustrating structures and devices to avoid complicating the disclosed principles. For clarity, not all features of the actual embodiment need to be described. Furthermore, the language used in this disclosure has been primarily chosen for readability and instructional purposes and may not have been chosen to define or limit the subject matter of the invention, thus requiring the necessary claims to determine such inventive subject matter. References to “an embodiment” or “an embodiment” in this disclosure mean that a particular feature, structure, or characteristic described in connection with that embodiment is included in at least one embodiment, and multiple references to “an embodiment” or “an embodiment” should not be construed as necessarily referring to the same embodiment.

[0029] Unless explicitly defined, the terms “a,” “an,” and “the” are not intended to refer to a singular entity, but rather to include a general category whose specific examples can be used for illustration. Therefore, the use of the terms “a” or “an” can mean any number of at least one, including “a,” “one or more,” “at least one,” and “one or more.” The term “or” means any of the options and any combination of the options, including all options unless explicitly indicated that the options are mutually exclusive. The phrase “at least one of” when combined with a list of items refers to a single item in the list or any combination of items in the list. The phrase does not require all items listed unless explicitly defined as such.

[0030] Reference Figure 1 This application discloses an adaptive measurement and control method for radio frequency channels, including the following steps S1-S4.

[0031] S1. During the operation of the data transmission terminal, three time-domain signals are acquired synchronously; wherein, the three time-domain signals include the digital baseband input signal X, the radio frequency feedback output signal Y after down-conversion and synchronization processing, and the instantaneous power supply voltage signal V at the power amplifier power supply terminal.

[0032] Specifically, the digital baseband input signal X typically originates from the baseband processing unit of the data transmission terminal and consists of a complex sequence of in-phase components I and quadrature components Q. This signal not only contains the modulation information to be transmitted but also serves as an ideal, distortion-free reference for subsequent nonlinear analysis. The acquisition path of the RF feedback output signal Y begins at the RF output of the power amplifier, where it is extracted via an RF coupler. The carrier frequency signal is then shifted to the intermediate frequency or baseband band via an RF receiving channel and a downconverter, and finally sampled by an analog-to-digital converter. To ensure that the RF feedback output signal can be compared with the digital baseband input signal in the same dimension, it must undergo frequency domain shifting and strict time synchronization processing to eliminate frequency deviations and group delay differences introduced by the hardware link.

[0033] The acquisition structure for the instantaneous power supply voltage signal V employs a high-bandwidth voltage probe or a dedicated independent analog-to-digital converter channel, with the connection point directly located at the drain or collector power supply pin of the power amplifier. This setup aims to construct a side-channel analysis mechanism that does not solely rely on the input and output data of the RF link, but rather captures the dynamic ripple characteristics of the power supply voltage terminal to reflect the transient response capability of the power system in the face of high-speed, highly dynamic RF loads in real time, thus providing a third-dimensional data source for decoupling the causes of nonlinear distortion. To achieve strict synchronization of the three signals, the system uses a unified reference clock source to drive each analog-to-digital converter and simultaneously activates the data capture window through a hardware trigger signal, ensuring that the sampling points of the digital baseband input signal X, the RF feedback output signal Y, and the instantaneous power supply voltage signal V correspond one-to-one on the time axis.

[0034] Taking a satellite data transmission terminal operating in the Ka band with an instantaneous bandwidth of 500MHz and using 16QAM modulation as an example, the nominal supply voltage of the power amplifier is 28V. During actual operation, when the baseband transmits a broadband modulated signal with a peak-to-average power ratio (PAPR), the power management unit, limited by its loop bandwidth and transient response speed, may be unable to maintain a constant voltage, causing the supply voltage to momentarily drop to 27.5V. At this time, step S1 will synchronously acquire the digital baseband IQ sequence within this time window, the RF feedback IQ sequence including nonlinear distortion, and the time-domain voltage waveform data that completely records the voltage drop from 28V to 27.5V and its recovery process.

[0035] S2. Construct a three-dimensional nonlinear distortion model based on the three time-domain signals, wherein the three-dimensional nonlinear distortion model describes the output of the power amplifier as a joint function of the input signal characteristics and the power supply voltage fluctuation.

[0036] Unlike traditional two-dimensional predistortion models that only map the relationship between the digital baseband input signal and the RF feedback output signal, three-dimensional nonlinear distortion models introduce the instantaneous power supply voltage signal as an independent variable into the modeling system. Traditional methods typically assume the power supply system is an ideal constant voltage source, treating the power amplifier as a time-invariant system. However, the three-dimensional model treats the power amplifier as a time-varying system controlled by the power supply voltage, acknowledging that the operating state of the device changes in real time with fluctuations in the supply voltage.

[0037] The joint function implies that the amplitude, phase, and other characteristics of the input signal are mathematically tightly coupled with the power supply voltage fluctuations. Here, voltage fluctuations are not considered additive background noise linearly superimposed on the output signal, but rather as a multiplicative modulation factor that directly alters the internal parameters of the power amplifier, such as the gain coefficient and phase offset. This means that the amplification capability of the power amplifier is no longer a fixed value, but a dynamic function jointly determined by the current input signal strength and the instantaneous supply voltage level.

[0038] Establishing such a joint function effectively decouples the power amplifier's own device characteristics from the influence of the power supply environment. In scenarios with unstable power supplies, the decrease in output power may be due to saturation caused by excessive signal amplitude or gain compression caused by insufficient supply voltage. Without decoupling, the system is highly susceptible to misinterpreting gain compression caused by voltage drops as drift in the nonlinear characteristics of the device itself, leading to incorrect predistortion parameter updates. The joint function allows the system to distinguish and quantify the distortion component caused by the specific factor of power supply voltage fluctuations, thereby preventing misinterpretation.

[0039] Specifically, step S2 includes the following sub-steps S21-S23.

[0040] S21. Extract the static mapping relationship between the digital baseband input signal X and the radio frequency feedback output signal Y, and construct a static nonlinear term characterizing the inherent distortion characteristics of the power amplifier under the reference rated voltage; wherein, the reference rated voltage is the nominal DC voltage value of the power supply of the power amplifier.

[0041] S22. Extract the fluctuation characteristics of the instantaneous power supply voltage signal V, and construct a dynamic power supply modulation term that characterizes the sensitivity of the power amplifier's nonlinear characteristics as the fluctuation of the instantaneous power supply voltage signal V changes.

[0042] S23. The dynamic power supply modulation term is superimposed on the static nonlinear term as a time-varying weighting coefficient to generate the three-dimensional nonlinear distortion model, such that the output response of the three-dimensional nonlinear distortion model includes dynamic gain compression prediction generated by the drop of the instantaneous power supply voltage signal V.

[0043] Static mapping relationships and static nonlinear terms reflect the original operating state of the power amplifier under ideal power supply conditions. They are typically described using a memory polynomial model, encompassing the device's nonlinear gain and memory effects. A reference rated voltage, such as 28V, serves as the model's reference zero or anchor point, determining the applicable voltage conditions for the static model. Extraction methods usually involve filtering data from periods with minimal power supply voltage fluctuations and fitting these data using the least squares method to obtain pure model parameters free from voltage fluctuation interference.

[0044] The specific algorithm for calculating fluctuation characteristics is usually the voltage value at the current sampling moment minus the reference rated voltage. The dynamic power supply modulation term is essentially a sensitivity gradient, representing the offset of the power amplifier's model coefficients for every 1V change in the power supply voltage, indicating the sensitivity of the device characteristics to voltage fluctuations.

[0045] The mathematical logic of superimposing time-varying weighted coefficients is that the total model coefficients equal the static coefficients plus the product of the dynamic power supply modulation term and the voltage fluctuation. This means that the model parameters dynamically change with real-time voltage fluctuations. This mechanism enables the model to accurately predict dynamic gain compression, that is, the model can calculate the output power decrease caused solely by a drop in power supply voltage, provided the input signal amplitude remains constant. For example, setting the reference rated voltage to 28V, the power amplifier's static gain to 30dB, and the voltage sensitivity to 0.5dB / V, if a voltage drop to 26V is detected at the current moment, resulting in a -2V fluctuation, the model will calculate that the actual gain at this time should be 30 plus -2 multiplied by 0.5, which is 29dB, thus predicting a 1dB dynamic gain compression.

[0046] S3. Based on the three-dimensional nonlinear distortion model, calculate the predistortion compensation parameters that dynamically change with the instantaneous power supply voltage signal V, and use the predistortion compensation parameters to perform real-time predistortion processing on the digital baseband input signal X to generate an RF drive signal and send it to the power amplifier.

[0047] Traditional static digital predistortion methods typically update model coefficients based on statistical data collected every few seconds or even minutes. This low-frequency update mechanism cannot handle power supply ripple at the microsecond level. Power supply voltage fluctuations, such as high-frequency noise in switching power supplies or transient drops caused by heavy loads, often occur within extremely short timescales, rendering static compensation strategies ineffective due to response lag. The requirement of "dynamically changing with the instantaneous power supply voltage signal V" refers to extremely high time resolution. That is, at each signal sampling point or within each data symbol period, the system refreshes the predistortion parameters based on the current voltage state to ensure that the compensation action is precisely aligned with the voltage fluctuation on the time axis.

[0048] Predistortion compensation parameters are typically expressed as a set of complex gain factors or bias values ​​of memory polynomial coefficients. These parameters are not fixed values, but are directly calculated from a three-dimensional nonlinear distortion model. The system inputs the real-time acquired instantaneous power supply voltage signal into the model, and dynamically calculates the optimal nonlinear correction coefficients to suit the current voltage level based on the voltage sensitivity relationship established in the model.

[0049] The generation of the RF drive signal follows a specific signal processing chain: the original digital baseband input signal X first enters the dynamic predistortion algorithm module, where it is processed using real-time updated compensation parameters to generate a predistorted baseband signal; this signal then undergoes digital-to-analog conversion and up-conversion to finally form the RF drive signal. A significant characteristic of this RF drive signal is that its waveform has been intentionally distorted or pre-amplified in the digital domain. This artificially introduced nonlinearity is to precisely adapt to and cancel the physical distortion that the power amplifier will produce, thereby ensuring that the output signal amplified by the power amplifier can be restored to an ideal linear waveform.

[0050] Specifically, step S3 includes the following sub-steps S31-S33.

[0051] S31. Monitor the instantaneous power supply voltage signal V in real time, and calculate the pre-distortion compensation parameter corresponding to the voltage drop amplitude of the instantaneous power supply voltage signal V relative to the reference rated voltage, based on the voltage sensitivity relationship established in the three-dimensional nonlinear distortion model.

[0052] S32. Generate an amplitude correction factor that corresponds inversely to the voltage drop amplitude based on the pre-distortion compensation parameters.

[0053] S33. The amplitude correction factor is applied to the digital baseband input signal X to generate the RF drive signal with pre-amplified amplitude to offset the power amplifier gain loss caused by the drop in the instantaneous power supply voltage signal V.

[0054] Real-time monitoring is achieved through continuous sampling via an analog-to-digital converter, ensuring the system can capture voltage fluctuations at the microsecond level. The application of voltage sensitivity is manifested in using the dynamic power modulation term extracted in step S2 to directly convert the measured voltage difference (current voltage minus the reference rated voltage) into the offset of the model coefficients. This process maps the external physical quantity of voltage fluctuations into adjustments to the model parameters of the internal algorithm.

[0055] The reverse correspondence means that if a voltage drop causes the power amplifier's gain curve to compress downwards (i.e., the output becomes smaller), then the generated correction factor must produce an upward gain expansion effect (i.e., the input becomes larger). The amplitude correction factor is typically a scalar or complex number with a magnitude greater than 1, used to simultaneously correct for amplitude attenuation and phase rotation.

[0056] Applying an amplitude correction factor to the digital baseband input signal X is typically achieved through multiplication; that is, the output signal equals the input signal multiplied by the correction factor. This operation pre-increases the signal amplitude in the digital domain, and the energy increment precisely fills the gain deficit caused by insufficient power supply in the analog domain power amplifier. In this way, the RF drive signal carries additional compensation energy, enabling the final RF output waveform to recover to an ideal linear state.

[0057] Following the previous embodiment, the reference rated voltage is set to 28V. When the monitoring system detects an instantaneous voltage drop to 26V, the voltage drop amplitude is calculated to be 2V. According to the three-dimensional nonlinear distortion model, if the voltage sensitivity is 0.5dB / V, the model extrapolates that this 2V drop will cause a 1dB gain loss in the power amplifier. Accordingly, the pre-distortion compensation parameter calculated by the system requires an increase of 1dB in the input signal power. This requirement translates to an amplitude correction factor of approximately 1.12, or 10 to the power of 20. The system multiplies the digital baseband input signal X by 1.12 and sends it to the power amplifier. Although the gain capability of the power amplifier decreases due to the power shortage, the final output power remains at the target linear value because the input signal amplitude has been pre-amplified, achieving transparent compensation for the voltage drop.

[0058] S4. Perform hierarchical closed-loop feedback optimization, adjust the peak characteristics of the digital baseband input signal X by calculating the cross-correlation coefficient between the RF output residual signal and the instantaneous power supply voltage signal V, and dynamically reconstruct the DC power supply voltage of the power amplifier power supply terminal according to the data transmission capability of the data transmission terminal; wherein, the RF output residual signal is determined based on the difference between the digital baseband input signal X and the RF feedback output signal Y.

[0059] The hierarchical closed-loop architecture comprises two levels of control logic. The first level is soft adjustment, primarily achieved by adjusting the peak characteristics of the digital baseband input signal, such as digital peak clipping. This method only requires modifying waveform data within the digital signal processing unit, without altering external hardware, thus offering fast response and low energy consumption. The second level is hard reconfiguration, involving adjusting the DC supply voltage at the power amplifier's power supply terminal. This method requires the power management unit to execute voltage regulation commands, involving the charging and discharging process of hardware circuitry, resulting in relatively slower response and higher energy consumption. There is a clear progressive relationship between the two levels; the system prioritizes soft adjustment to address minor linearity issues, only escalating to hard reconfiguration when soft adjustment fails to meet performance requirements.

[0060] The reason for choosing the cross-correlation coefficient as the criterion is that it can effectively distinguish the source of RF distortion. The RF output residual signal represents the nonlinear error that remains after pre-distortion processing. If there is a high cross-correlation between this residual signal and the instantaneous power supply voltage signal V, it indicates that the waveform trend of the residual error is highly consistent with the fluctuation of the power supply voltage, thus determining that the current distortion is mainly caused by insufficient power supply capacity. Conversely, if the cross-correlation coefficient is low, it indicates that the residual error is unrelated to power supply fluctuations, and the distortion may originate from inaccurate parameter fitting or non-convergence of the nonlinear distortion model itself. This mechanism ensures that subsequent control strategies can accurately target the power supply as a specific source of interference.

[0061] Specifically, step S4 includes the following sub-steps S41-S44.

[0062] S41. Obtain the radio frequency output residual signal after pre-distortion processing, and calculate the cross-correlation coefficient between the radio frequency output residual signal and the instantaneous power supply voltage signal V.

[0063] S42. Compare the cross-correlation coefficient with a preset correlation threshold. If the cross-correlation coefficient is greater than the correlation threshold, it is determined that the current distortion is mainly caused by insufficient power supply capacity, and the peak clipping control strategy is adjusted to reduce the peak-to-average power ratio of the digital baseband input signal X until the cross-correlation coefficient drops below the correlation threshold.

[0064] The process of calculating the cross-correlation coefficient is essentially a mathematical diagnosis, using statistical methods to quantify the similarity in waveform variation trends between the RF output residual signal and the instantaneous power supply voltage signal V. This step is used to accurately pinpoint the cause of communication quality degradation. If the two show a strong correlation, it indicates that the error is directly controlled by the fluctuation trajectory of the power supply voltage.

[0065] The decision logic is based on a preset correlation threshold, such as 0.7. When the calculated cross-correlation coefficient exceeds this value, the system confirms that power instability has become the primary constraint on linearity. The triggered peak-shaving control strategy, which adjusts the peak-to-average power ratio (PAPR) of the digital baseband input signal X, produces a direct hardware response. Reducing the peak power of the signal directly lowers the power amplifier's demand for instantaneous high current, thereby reducing voltage drop and ripple amplitude in the power supply loop, eliminating the physical cause of voltage sag at its source. This strategy does not merely address the signal processing level but improves the power supply environment by altering load characteristics.

[0066] The iterative negative feedback control logic of the system is demonstrated when the cross-correlation coefficient drops below the correlation threshold. The system does not drastically reduce the signal peak value all at once, but rather uses a step-by-step adjustment. Each time the peak-to-average power ratio (PAPR) is reduced by one level, the system recalculates the cross-correlation coefficient. If the coefficient is still higher than the threshold, the PAPR continues to decrease; once the coefficient falls below the threshold, the adjustment stops immediately. This mechanism ensures that the system can achieve a linearly stable state that meets the requirements with minimal signal quality loss.

[0067] For example, the correlation threshold is set to 0.6. At a certain moment, the calculated cross-correlation coefficient is 0.85, indicating that power supply ripple is severely affecting signal quality. The system initiates a peak-to-average power ratio (PAPR) strategy, reducing the PPR of the digital baseband input signal from 8dB to 7dB. As the peak current decreases, the power supply voltage ripple also decreases, and the recalculated cross-correlation coefficient drops to 0.55. Since this value is below the correlation threshold, the system determines that the power supply interference has been effectively suppressed, and then stops peak clipping adjustment, maintaining the current signal configuration.

[0068] Optionally, step S42 includes the following sub-steps S421-S424.

[0069] S421. Call the dynamic power supply modulation term in the three-dimensional nonlinear distortion model to calculate the dynamic saturation input boundary allowed for the power amplifier to maintain linear operation under the fluctuation state of the current instantaneous power supply voltage signal V.

[0070] S422. Configure the dynamic saturation input boundary as a time-varying threshold for the peak-shaving control strategy.

[0071] S423. The digital baseband input signal X is judged point by point using the time-varying threshold, and amplitude compression is performed only on signal sampling points whose amplitude exceeds the dynamic saturation input boundary, thereby reducing the peak-to-average power ratio while maximizing the preservation of the waveform characteristics of the digital baseband input signal X that does not exceed the dynamic saturation input boundary.

[0072] Recalculate the cross - correlation coefficient between the radio - frequency output residual signal and the instantaneous power - supply voltage signal V. If the recalculated cross - correlation coefficient is still greater than the correlation threshold, then repeat the execution of S421 to S423 based on the updated fluctuation state of the instantaneous power - supply voltage signal V until the cross - correlation coefficient drops below the correlation threshold.

[0073] Different from the one - size - fits - all mode with a fixed threshold in traditional peak - clipping techniques, this step uses the three - dimensional nonlinear distortion model established in step S2 to inversely deduce the physical linear limit of the power amplifier under the current voltage state. For example, model calculations show that at the moment of the current voltage drop, the power amplifier can only linearly amplify an input signal with an amplitude not exceeding 0.8V, and this 0.8V is the dynamic saturation input boundary at this moment.

[0074] The peak - clipping control strategy implements a time - varying clipping logic that varies with voltage fluctuations based on this dynamic boundary. When the power - supply voltage is at a low level, the peak - clipping threshold decreases accordingly, and strict amplitude compression is performed; when the power - supply voltage returns to normal, the peak - clipping threshold increases accordingly, relaxing the signal - amplitude limit. Using the time - varying threshold for point - by - point discrimination ensures that only the signal spikes that exceed the physical bearing capacity and will inevitably cause distortion are cut off, while completely retaining other signal sampling points within the linear working area, thus maximizing the waveform integrity of the original signal while suppressing the cross - correlation coefficient.

[0075] If, after one round of peak - clipping, the cross - correlation coefficient is still higher than the correlation threshold, it indicates that the current compression strength is insufficient to eliminate the nonlinear effects caused by power - supply fluctuations, or the power - supply voltage has dropped more significantly. The system will enter the next round of more aggressive boundary calculation and signal - compression process based on the latest voltage - fluctuation state until the radio - frequency output residual is decoupled from the power - supply voltage.

[0076] S43. After adjusting the peak - clipping control strategy, monitor the effective data - throughput index of the data - transmission terminal in real time.

[0077] S44. If the effective data - throughput index is lower than the preset service compliance line, generate a hardware control instruction and send it to the power - management unit of the data - transmission terminal to control the power - management unit to increase the DC voltage reference value applied to the power - amplifier power - supply terminal, and restore the peak - clipping control strategy to the initial state after the DC voltage reference value is increased; where the initial default value of the DC voltage reference value is equal to the reference rated voltage.

[0078] Real-time monitoring of effective data throughput metrics constitutes a cost-benefit assessment mechanism for digital peak clipping strategies. While excessive peak clipping can suppress power supply ripple, it inevitably leads to a deterioration in the error vector amplitude of the transmitted signal and distortion of the constellation diagram. This degradation in signal quality increases the bit error rate of demodulation at the receiver, thereby triggering the data packet retransmission mechanism at the link layer, ultimately resulting in a significant decrease in the effective data transmission rate.

[0079] The judgment logic sets a specific service performance threshold, such as 500Mbps. When the monitored throughput falls below this threshold, it indicates that the current soft-tuning strategy has sacrificed too much signal detail to maintain linearity. Relying solely on digital domain processing can no longer simultaneously meet the requirements of linearity and data rate, and the system must initiate a hard reconfiguration mechanism. At this point, a hardware control command is sent to instruct the power management unit to perform a boost operation, for example, increasing the DC voltage reference value from 28V to 29V.

[0080] The principle behind increasing the voltage lies in directly raising the upper limit of the power amplifier's saturated output power, thereby physically expanding the dynamic range of its linear operating region. After successfully raising the DC voltage reference value, the power amplifier's physical tolerance is enhanced, eliminating the need to compress the input signal to accommodate power supply capabilities. Therefore, the system executes a reset mechanism, restoring the peak clipping control strategy to its initial state, i.e., stopping peak clipping, thus restoring full-rate transmission with a high signal-to-noise ratio. This mechanism achieves a global dynamic balance between energy efficiency and performance: maintaining a lower voltage under normal loads to save energy, and only consuming more energy to achieve necessary communication performance under extreme conditions where throughput is limited.

[0081] Optionally, S44 includes the following sub-steps S441-S444.

[0082] S441. Based on the static nonlinear term in the three-dimensional nonlinear distortion model, determine the theoretical saturated output power of the power amplifier at the preset linearity target value.

[0083] S442. Combining the dynamic gain compression prediction output by the three-dimensional nonlinear distortion model, calculate the current power backoff value caused by the drop in the instantaneous power supply voltage signal V, and use the voltage sensitivity relationship to reverse map the power backoff value into a voltage compensation increment.

[0084] S443. The voltage compensation increment is superimposed on the current DC voltage reference value to generate the hardware control command, so that the improved hardware power supply voltage compensation is reduced by the linearity loss characterized by the dynamic gain compression prediction.

[0085] S444. After detecting that the power management unit has executed the hardware control instruction, reset the time-varying threshold in the peak clipping control strategy to the initial default value.

[0086] Determining the theoretical saturated output power is to establish the upper limit of the power amplifier under ideal power supply conditions. This indicator represents the maximum output capability that the power amplifier can achieve under reference rated voltage while meeting linearity indicators such as error vector magnitude or adjacent channel power ratio. The calculation is directly derived from the static nonlinear term constructed in step S21, because this term eliminates the interference of power supply fluctuations and can accurately reflect the inherent physical characteristics of the device under optimal factory conditions.

[0087] By combining dynamic gain compression predictions from a three-dimensional nonlinear distortion model, the system can quantify the specific degree to which a current voltage drop weakens output capability. For example, model calculations show that under the current low voltage condition, the actual saturation power decreases by a certain number of decibels compared to the theoretical value. This difference is the power backoff value, representing the transmit power margin that is forcibly sacrificed to maintain linearity. Utilizing voltage sensitivity relationships, the system inversely maps this power deficit to a voltage compensation requirement. This mapping process follows a specific functional relationship: if device characteristics show that the saturation power increases by 0.5 dB for every 1V increase in voltage, the system uses this ratio to convert the power backoff value into a voltage compensation increment.

[0088] The generated hardware control instructions are typically encapsulated in I2C or SPI communication protocol format, containing the new voltage value to be written to the power management chip's DAC register. By adding the voltage compensation increment to the current DC voltage reference value, the bias voltage applied to the drain or collector of the power amplifier is physically increased. This operation increases the transistor's conduction angle or output swing limit, physically expanding the saturation region boundary, allowing signal peaks that were previously compressed due to insufficient voltage to now pass through the linear range completely.

[0089] Because of the millisecond-level response delay in power supply hardware regulation, the system must wait until it detects that the power supply voltage has indeed been increased before proceeding to the next step. This is because, since the physical power supply capability has been enhanced, the peak clipping limits previously applied to protect linearity are no longer necessary. Resetting the time-varying threshold in the peak clipping control strategy to its initial default value means canceling the artificial amplitude compression, allowing the signal to pass at full speed, thereby restoring a high signal-to-noise ratio. This reflects a control strategy that avoids using software lossy compression when the problem can be solved through hardware improvements.

[0090] Based on the above process, the reference rated voltage is set to 28V, and the required linear output power is 40dBm. Static nonlinearity indicates that the power amplifier can output 40dBm at 28V. When a voltage drop to 26V is detected, the model predicts that only a linear output of 38dBm is possible, resulting in a 2dB power backoff. Given a voltage sensitivity of 1dB / V, a 2V compensation is calculated. The system generates a command to adjust the DC voltage reference value from 28V to 30V to mitigate future voltage drops and compensate for current losses. Once the power management unit completes its execution and the voltage rises to 30V, the system immediately stops peak clipping, and data throughput returns to its maximum value.

[0091] It should be understood that the sequence number of each step in the above embodiments does not imply the order of execution. The execution order of each process should be determined by its function and internal logic, and should not constitute any limitation on the implementation process of the embodiments of the present invention.

[0092] In one embodiment, a computer device is provided, including a memory, a processor, and a computer program stored in the memory and executable on the processor. When the processor executes the computer program, it implements the radio frequency channel adaptive measurement and control method of the above embodiment.

[0093] In one embodiment, a computer-readable storage medium is provided, on which a computer program is stored, which, when executed by a processor, implements the radio frequency channel adaptive measurement and control method of the above embodiment.

[0094] Those skilled in the art will understand that all or part of the processes in the methods of the above embodiments can be implemented by a computer program instructing related hardware. This computer program can be stored in a non-volatile computer-readable storage medium. When executed, the computer program can include the processes of the embodiments of the above methods. Any references to memory, storage, databases, or other media used in the embodiments of this application can include non-volatile and / or volatile memory. Non-volatile memory can include read-only memory (ROM), programmable ROM (PROM), electrically programmable ROM (EPROM), electrically erasable programmable ROM (EEPROM), or flash memory. Volatile memory can include random access memory (RAM) or external cache memory. By way of illustration and not limitation, RAM is available in various forms, such as static RAM (SRAM), dynamic RAM (DRAM), synchronous DRAM (SDRAM), dual data rate SDRAM (DDRSDRAM), enhanced SDRAM (ESDRAM), synchronous link DRAM (SLDRAM), Rambus direct RAM (RDRAM), direct memory bus dynamic RAM (DRDRAM), and memory bus dynamic RAM (RDRAM), etc.

[0095] Those skilled in the art will clearly understand that, for the sake of convenience and brevity, the above-described division of functional units and modules is used as an example. In practical applications, the above functions can be assigned to different functional units and modules as needed, that is, the internal structure of the device can be divided into different functional units or modules to complete all or part of the functions described above.

[0096] The above embodiments are only used to illustrate the technical solutions of the present invention, and are not intended to limit it. Although the present invention has been described in detail with reference to the foregoing embodiments, those skilled in the art should understand that modifications can still be made to the technical solutions described in the foregoing embodiments, or equivalent substitutions can be made to some of the technical features. Such modifications or substitutions do not cause the essence of the corresponding technical solutions to deviate from the spirit and scope of the technical solutions of the embodiments of the present invention, and should all be included within the protection scope of the present invention.

Claims

1. A radio frequency channel adaptive measurement and control method, characterized in that, Includes the following steps: S1. During the operation of the data transmission terminal, three time-domain signals are acquired synchronously; wherein, the three time-domain signals include the digital baseband input signal X, the radio frequency feedback output signal Y after down-conversion and synchronous processing, and the instantaneous power supply voltage signal V at the power amplifier power supply terminal; S2. Construct a three-dimensional nonlinear distortion model based on the three time-domain signals, wherein the three-dimensional nonlinear distortion model describes the output of the power amplifier as a joint function of the input signal characteristics and the power supply voltage fluctuation; S3. Based on the three-dimensional nonlinear distortion model, calculate the predistortion compensation parameters that dynamically change with the instantaneous power supply voltage signal V, and use the predistortion compensation parameters to perform real-time predistortion processing on the digital baseband input signal X to generate an RF drive signal and send it to the power amplifier; S4. Perform hierarchical closed-loop feedback optimization, adjust the peak characteristics of the digital baseband input signal X by calculating the cross-correlation coefficient between the RF output residual signal and the instantaneous power supply voltage signal V, and dynamically reconstruct the DC power supply voltage of the power amplifier power supply terminal according to the data transmission capability of the data transmission terminal; wherein, the RF output residual signal is determined based on the difference between the digital baseband input signal X and the RF feedback output signal Y.

2. The radio frequency channel adaptive measurement and control method according to claim 1, characterized in that, Step S2 includes the following sub-steps: S21. Extract the static mapping relationship between the digital baseband input signal X and the radio frequency feedback output signal Y, and construct a static nonlinear term characterizing the inherent distortion characteristics of the power amplifier under the reference rated voltage; wherein, the reference rated voltage is the nominal DC voltage value of the power supply of the power amplifier; S22. Extract the fluctuation characteristics of the instantaneous power supply voltage signal V, and construct a dynamic power supply modulation term that characterizes the sensitivity of the power amplifier's nonlinear characteristics as the fluctuation of the instantaneous power supply voltage signal V changes; S23. The dynamic power supply modulation term is superimposed on the static nonlinear term as a time-varying weighting coefficient to generate the three-dimensional nonlinear distortion model, such that the output response of the three-dimensional nonlinear distortion model includes dynamic gain compression prediction generated by the drop of the instantaneous power supply voltage signal V.

3. The radio frequency channel adaptive measurement and control method according to claim 2, characterized in that, Step S3 includes the following sub-steps: S31. Monitor the instantaneous power supply voltage signal V in real time, and calculate the pre-distortion compensation parameter corresponding to the voltage drop amplitude of the instantaneous power supply voltage signal V relative to the reference rated voltage, based on the voltage sensitivity relationship established in the three-dimensional nonlinear distortion model. S32. Generate an amplitude correction factor that corresponds inversely to the voltage drop amplitude based on the pre-distortion compensation parameters; S33. The amplitude correction factor is applied to the digital baseband input signal X to generate the RF drive signal with pre-amplified amplitude to offset the power amplifier gain loss caused by the drop in the instantaneous power supply voltage signal V.

4. The radio frequency channel adaptive measurement and control method according to claim 3, characterized in that, Step S4 includes the following sub-steps: S41. Obtain the radio frequency output residual signal after pre-distortion processing, and calculate the cross-correlation coefficient between the radio frequency output residual signal and the instantaneous power supply voltage signal V; S42. Compare the cross-correlation coefficient with a preset correlation threshold. If the cross-correlation coefficient is greater than the correlation threshold, it is determined that the current distortion is mainly caused by insufficient power supply capacity, and the peak clipping control strategy is adjusted to reduce the peak-to-average power ratio of the digital baseband input signal X until the cross-correlation coefficient drops below the correlation threshold. S43. After implementing the adjustment of the peak-shaving control strategy, monitor the effective data throughput index of the data transmission terminal in real time; S44. If the effective data throughput indicator is lower than the preset service compliance line, a hardware control command is generated and sent to the power management unit of the data transmission terminal to control the power management unit to increase the DC voltage reference value applied to the power amplifier power supply terminal, and after the DC voltage reference value is increased, the peak clipping control strategy is restored to the initial state; wherein, the initial default value of the DC voltage reference value is equal to the reference rated voltage.

5. The radio frequency channel adaptive measurement and control method according to claim 4, characterized in that, S42 includes the following sub-steps: S421. Call the dynamic power supply modulation term in the three-dimensional nonlinear distortion model to calculate the dynamic saturation input boundary allowed for the power amplifier to maintain linear operation under the fluctuation state of the current instantaneous power supply voltage signal V. S422. Configure the dynamic saturation input boundary as a time-varying threshold for the peak-shaving control strategy; S423. The digital baseband input signal X is judged point by point using the time-varying threshold, and amplitude compression is performed only on signal sampling points whose amplitude exceeds the dynamic saturation input boundary, thereby reducing the peak-to-average power ratio while maximizing the preservation of the waveform characteristics of the digital baseband input signal X that does not exceed the dynamic saturation input boundary; S424. Recalculate the cross-correlation coefficient between the RF output residual signal and the instantaneous power supply voltage signal V. If the recalculated cross-correlation coefficient is still greater than the correlation threshold, repeat S421 to S423 based on the updated fluctuation state of the instantaneous power supply voltage signal V until the cross-correlation coefficient drops below the correlation threshold.

6. The radio frequency channel adaptive measurement and control method according to claim 5, characterized in that, S44 includes the following sub-steps: S441. Based on the static nonlinear term in the three-dimensional nonlinear distortion model, determine the theoretical saturated output power of the power amplifier at the preset linearity target value; S442. Combining the dynamic gain compression prediction output by the three-dimensional nonlinear distortion model, calculate the current power backoff value caused by the drop in the instantaneous power supply voltage signal V, and use the voltage sensitivity relationship to reverse map the power backoff value into a voltage compensation increment. S443. The voltage compensation increment is superimposed on the current DC voltage reference value to generate the hardware control command, so that the improved hardware power supply voltage compensation is affected by the linearity loss characterized by the dynamic gain compression prediction. S444. After detecting that the power management unit has executed the hardware control instruction, reset the time-varying threshold in the peak clipping control strategy to the initial default value.

7. A computer device, characterized in that, It includes: One or more processors; Memory; One or more applications, wherein the one or more applications are stored in the memory and configured to be executed by the one or more processors, the one or more applications being configured to: perform the radio frequency channel adaptive measurement and control method according to any one of claims 1 to 6.

8. A computer-readable storage medium, characterized in that, The storage medium stores at least one instruction, at least one program, code set, or instruction set, wherein the at least one instruction, the at least one program, the code set, or the instruction set is loaded and executed by a processor to implement the radio frequency channel adaptive measurement and control method as described in any one of claims 1 to 6.

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