H-bridge and method for its operation in an LED headlight using an LED light source and high pulsed operating voltages and method for its operation

Abstract

Device for controlling at least one light-emitting diode (LED1) to generate short light pulses (LP),- with an H-bridge (H) consisting of a first half-bridge (HB1: T1, T2) with a first transistor (T1) and a second transistor (T2) and a second half-bridge (HB2: T2, T3) with a third transistor (T3) and a fourth transistor (T4),- wherein the H-bridge (H) is controlled by a control unit (ST) and- wherein the H-bridge (H) can be operated by the control unit (ST) in pulsed mode (GPB) and in quasi-continuous mode (QDB) and- wherein the first half-bridge (HB1: T1, T2) is supplied with electrical energy from a first positive supply voltage (VCC1) and a first negative supply voltage (GND1) and- wherein the second half-bridge (HB2: T3,T4) is supplied with electrical energy from a second positive supply voltage (VCC2) and a second negative supply voltage (GND2) and- wherein the light-emitting diode (LED1) is connected with its cathode (K) to the output of the first half-bridge (HB1: T1, T2) and- wherein the light-emitting diode (LED1) is connected with its anode (A) to the output of the second half-bridge (HB2: T3, T4) and- wherein the first positive supply voltage (VCC1) and the second positive supply voltage (VCC2) can be equal and- wherein the first negative supply voltage (GND1) and the second negative supply voltage (GND2) can be equal and- wherein the light source, in particular the one or more light-emitting diodes (LED1), represents the load of the H-bridge (H) between the output of the first half-bridge (HB1: T1, T2) and the output of the second half-bridge (HB2: T3, T4) and- wherein the control device (ST) is designed to operate in pulsed mode (GPB) a “PAn” condition,in which a forward voltage in the forward direction of the light-emitting diode (LED1) is applied to the light-emitting diode (LED1) through the H-bridge (H), is not maintained by the H-bridge (H) for longer than a turn-on time (τpp), and- wherein the control device (ST) is designed so that in pulsed operation (GPB) a "PAus" state, in which a reverse voltage against the forward direction of the light-emitting diode (LED1) is applied to the light-emitting diode (LED1) through the H-bridge (H), is not maintained by the H-bridge (H) for longer than a clearing time (τpn), and- wherein the clearing time (τpn) is less than the charge carrier lifetime (τ) in the PN junction of the light-emitting diode (LED1), and- wherein the turn-on time (τpp) is less than the charge carrier lifetime (τ) in the PN junction of the light-emitting diode (LED1).

Description

Field of invention The proposed method and devices relate to the generation of short light pulses by controlling at least one light-emitting diode, hereinafter also referred to as LED. General Introduction LiDAR will play a crucial role in ADAS and autonomous driving in the future. Stringent functional safety requirements necessitate reliable and sensitive systems to ensure correct decisions can be made in extreme situations. The short light pulses required for this are essential in many applications. If necessary, more expensive laser diodes are often used to enable pulses shorter than approximately 10 ns. A primary application for pulsed light sources is time-of-flight measurement for distance determination (e.g., Flash LiDAR). Since the measurement information is contained in the pulse edges, shortening the pulse length directly improves efficiency, which translates into improved performance. Particularly in long-range LiDAR systems, system performance is limited by the permissible emission power.An efficient light source is therefore at least as crucial for system performance as a sensitive sensor. Generally, LiDAR systems use laser beams that can be deflected by mirrors. However, this creates the problem of high energy density. This can damage the eyes. Flash LIDAR systems are currently implemented with dedicated infrared pulse sources and their range and sensitivity are limited by a legally restricted transmission power to ensure eye safety. Short light pulses from pulsed light sources are therefore of paramount importance for time-of-flight measurements used to determine distances. The efficiency of such time-of-flight measurements is determined by the pulse length in certain methods. Shortening the pulse length increases efficiency, as a greater range can then be achieved with a constant average light intensity. State of the art Automotive lidar systems are generally built with dedicated light sources today. For reasons of public acceptance, this limits them to the invisible wavelength range and necessitates small dimensions in relation to the available installation space in vehicles. Both of these limitations, considering eye safety, reduce the maximum transmission power and thus the system's performance. An increase in range is urgently needed. As explained below, a key issue is the generation of short light pulses using light-emitting diodes (LEDs) or laser diodes. LED pulses are generated using switchable current or voltage sources, according to current technology. This typically results in rise and fall times on the order of 10 ns. These are caused by the charging and discharging of the junction capacitance in conjunction with parasitic components of the diode and its terminals. From EP 0 470 780 A2, a device for improving the pulse shape of an LED is known. An H-bridge consisting of four bipolar transistors (Fig. 1 of EP 0 470 780 A2 and their reference numerals 12, 14, 24, 26) is used to drive an LED (reference numeral 18 of EP 0 470 780 A2). The H-bridge disclosed in EP 0 470 780 A2 has the disadvantage that it requires two resistors in the reverse bias (reference numerals 20 and 22 of EP 0 470 780 A2) to limit cross-currents occurring in the two H-bridges as a result of its use. (See column 2, lines 49 to 51 of EP 0 470 780 A2). This significantly limits the switching-off behavior of the driver circuit proposed in EP 0 470 780 A2 compared to the method and device proposed here.Furthermore, the circuit proposed in EP 0 470 780 A2 includes a current source (reference numeral 16 of EP 0 470 780 A2) which requires the integration of at least one additional current source transistor into the circuit. The H-bridge of EP 0 470 780 A2 is therefore not voltage-supplied, but rather current-supplied from the aforementioned current source (reference numeral 16 of EP 0 470 780 A2). This additional current source necessitates additional chip area when integrated into an integrated microelectronic circuit.According to the technical teaching of EP 0 470 780 A2, the LED is operated in the off state by switching off the first high-side transistor of the first half-bridge (reference numeral 24 of EP 0 470 780 A2) and switching off the second high-side transistor of the second half-bridge (reference numeral 26 of EP 0 470 780 A2) and switching on the first low-side transistor of the first half-bridge (reference numeral 12 of EP 0 470 780 A2) and switching off the second low-side transistor of the second half-bridge (reference numeral 14 of EP 0 470 780 A2). In the switched-off state, according to the technical teaching of EP 0 470 780 A2, the light-emitting diode (reference numeral 18 of EP 0 470 780 A2) is connected to the current source (reference numeral 16 of EP 0 470 780 A2) only at its anode via the first low-side transistor of the first half-bridge (reference numeral 12 of EP 0 470 780 A2). Reference is made here to the timing diagrams in Fig. 1 of EP 0 470 780 A2.The LED (reference numeral 18 of EP 0 470 780 A2) is therefore not connected to a power source when switched off, since the cathode of the LED is not connected in this state according to the technical teaching of EP 0 470 780 A2. The technical teaching of EP 0 470 780 A2 now provides for the optimization of the switch-on behavior of the LED (reference numeral 18 of EP 0 470 780 A2). Shortly after the first high-side transistor (reference 24 of EP 0 470 780 A2) and the second low-side transistor (reference 14 of EP 0 470 780 A2) are switched on, the second high-side transistor (reference 26 of EP 0 470 780 A2) switches on after a delay τ and takes over part of the current from the power source (reference 16 of EP 0 470 780 A2). Switch-off occurs exclusively via the first low-side transistor (reference 12 of EP 0 470 780 A2).A particular disadvantage is that the discharge current is limited by the current source (reference numeral 16 of EP 0 470 780 A2), meaning that the charge QLED=CLED*ULEDin of the LED (reference numeral 18 of EP 0 470 780 A2) can only be switched off within the defined time tLEDaus= QLED / Isource=CLED*ULED / Isourceaus. The discharge process is hindered and therefore intensified by the resistors (reference numerals 20 and 22 of EP 0 470 780 A2). A device according to the technical teaching of EP 0 470 780 A2 is thus suitable for producing a particularly steep increase in light output. However, the circuit is not suitable for generating a short light pulse from an LED. The technical teaching of EP 0 470 780 A2 therefore does not solve the problem of generating ultrashort light pulses using an LED. From WESEN, Bjorn [et al.]: “Fastest way of doing on / off-modulation of an LED?”. June 22, 2011, edited June 23, 2014. 4th p. URL: https: / / electronics.stackexchange.com / questions / 15818 / fastest-way-ofdoing-on-off-modulation-of-a-led [accessed January 23, 2018], the use of two half-bridges for driving an LED is known. From “TPS28226 High-Frequency 4-A Sink Synchronous MOSFET Drivers”, an application note from Texas Instruments, and “2A Synchronous Buck Power MOSFET Driver”, an application note from Microchip for the Microchip product MCP14628, half-bridge drivers without LED use are known. From this, a half-bridge control without the current source of the EP 0 470 780 A2 can be constructed in the overall view. Such an H-bridge circuit for controlling LED light sources of different colors and polarities is known from EP 2 761 978 B1. However, in this case, the polarity reversal serves to select different colors. In the technical teaching of EP 2 761 978 B1, the LEDs of different colors are polarized differently, so that the voltage polarity reversal leads to a change in the emitted color of the entire device. The device of EP 2 761 978 B1 is therefore not suitable or intended for emitting short light pulses. From EP 0 762 651 A2, it is known to switch on an LED with an initially higher current followed by a lower operating current to achieve steep switch-on edges. A dimming circuit for LED lighting is known from DE 10 2016 116 718 A1. The combination of a light pulse source with a TOF camera is known, for example, from DE 10 2014 105 482 A1. Taken together, the above-mentioned publications only solve the problem of a short rise time, not a short light pulse. They certainly do not solve the problem of the large charge that needs to be dissipated when switching off LEDs, which are typically large in area and therefore in capacitance. The publications mentioned above, insofar as they deal with pulse shaping, focus on controlling LEDs and laser diodes designed and optimized for signal transmission. The capacitance problem of LEDs, which hinders their use as measuring instruments, remains unsolved by all the publications listed above, even when considered together. From WO 2014 / 124 768 A1, a method for a vehicle is known that includes detecting the vehicle's operating state, generating a modulated signal depending on the operating state, and controlling a lighting device of the vehicle depending on the modulated signal. According to the technical teaching of WO 2014 / 124 768 A1, the lighting device is designed to illuminate a scene in the vehicle's surroundings or within the vehicle. The method of WO 2014 / 124 768 A1 further includes receiving light emitted by the lighting device and reflected by an object in the scene, generating a received signal depending on the received light, and determining distance information for the object depending on the modulated signal and the received signal.The technical teaching of WO 2014 / 124 768 A1 leaves open how particularly short pulses, which are required for good depth resolution, are to be generated. From EP 2 160 629 B1, a method for providing driver assistance is known in which, among other things, a visible light source in the form of a light-emitting diode is driven such that pulsating light is emitted in a predefined mode using the drive data. The illumination function is maintained despite the pulsation. According to the technical teaching of EP 2 160 629 B1, objects in the illuminated area can be detected using the pulses emitted in this way, and subsequently, vehicle functions and / or driver actions can be triggered by the detected data. German patent DE 10 2006 044 794 A1 discloses a vehicle-based lidar system in which the transmitter unit is integrated into the vehicle's headlights. However, the technical teaching of DE 10 2006 044 794 A1 does not specify how the particularly short pulses required for good depth resolution are to be generated. DE 10 2016 205 563 A1 discloses a lighting device for a vehicle and a vehicle headlight. The lighting device for a vehicle according to the technical teaching of DE 10 2016 205 563 A1 is equipped with a light source that can emit useful light and / or auxiliary light into an environment, with a sensor that can at least partially detect useful light and / or auxiliary light reflected from the environment, and with electronics for evaluating the useful light and / or auxiliary light detected by the sensor. The technical teaching of DE 10 2016 205 563 A1 also leaves open how the particularly short pulses required for good depth resolution are to be generated. DE 20 2013 008 067 U1 discloses a method for controlling LEDs of a headlight based on a sensor that detects the light from the LED, whereby the control of the LED is changed depending on the detected light signal. DE 10 2013 001 273 A1 discloses such a device in which the LED itself is used as a photodetector for this purpose. German patent DE 10 2013 002 668 A1 discloses the use of a vehicle's lighting system as a distance and speed measuring system. However, the technical teaching of DE 10 2013 002 668 A1 does not reveal how the pulses can be made particularly short. CN 102 612 231 A discloses the control of an LED module with two antiparallel connected LED strings. According to the technical teaching of CN 102 612 231 A (see, for example, section

[0004] of CN 102 612 231 A), the two LED strings are to have different color temperatures and are controlled and operated via an H-bridge. The function of the H-bridge is to reverse the current direction and thus utilize the current direction characteristics of the LEDs for selecting the different LED strings during operation. The technical teaching of CN 102 612 231 A also leaves open how the particularly short pulses required for good depth resolution are to be generated. A similar method for selecting between two different antiparallel connected LEDs by means of polarity reversal using an H-bridge is known from DE 10 2006 041 013 A1. The use of an H-bridge to control an LED, specifically an organic LED, is also known from JP 2005 - 158 483 A. Controlling the LED with blocking pulses is also described there. It states: “As shown, for example, in Fig. 8, its preferred design is to supply the forward current into the electroluminescent component (reference numeral 10 of JP 2005 - 158 483 A) with a control pulse (reference numeral b of JP 2005 - 158 483 A), which switches the switching means in the form of the first transistor (reference numeral Tr1 of JP 2005 - 158 483 A), and which is supplied intermittently by the control devices (reference numeral 22 of JP 2005 - 158 483 A). In this way [...] the electroluminescent component (reference numeral 10a of JP 2005 - 158 483 A) [...] can be made to be switched on repeatedly by inverse control pulses from the control device (reference numeral 22 of JP 2005 - 158 483 A ) [...] are generated.“The technical teaching of JP 2005 - 158 483 A also leaves open how particularly short pulses, which are required for good depth resolution, are to be generated. The transmission of data between vehicles and infrastructure devices using headlights and taillights is known from US 2016 / 0 257 306 A1 and DE 10 2016 202 505 A1. From DE 10 2013 001 274 A1 a method for controlling a matrix LED headlight is known in which this photodetector property of an LED biased in the reverse direction is also utilized. From US patent 4,571,506 A, a device and an associated method for rapidly modulating the light emission of an LED are known. In this method, an LED (reference number LED in US patent 4,571,506) is brought to a DC operating point by an unmodulated current from a current source (“Precision Current Regulator” in Fig. 2 of US patent 4,571,506 A). This DC operating point is stabilized by a series-connected inductor (reference number L2 in US patent 4,571,506 A). An additional modulated small-signal current is superimposed on the LED current by a modulated bipolar current source (transistor with reference numbers Q4 and Q3 in US patent 4,571,506 A) connected to the same LED terminal. A capacitor (reference number CI of US 4 571 506 A in its Fig. 2) differentiates one of the two differential control signals and thus provides a short undershoot below the 0-V line during the switch-off process, which then returns to a positive low signal value.This ensures faster clearing of the relevant space charge region of the LED. Furthermore, it is already known from US 4 571 506 A (column 2, lines 59 to 65 of US 4 571 506 A) that higher reverse voltage values ​​accelerate the clearing of the space charge region. According to the prior art and, for example, the technical teaching of US 4 571 506 A, this reverse voltage can only assume a limited value without damaging the LED (e.g., column 2, lines 27 to 36 of US 4 571 506 A). From DE 197 04 496 A1 it is known that the modulation of the sensitivity of light sensors by a control system is known. A multicolor LED is known from US 9 653 642 B1. Its use in headlights is proposed. From DE 10 2015 110 233 A1, an image generation device is known which generates a color image by sequentially emitting different illumination colors and recording the corresponding images. The use of a headlight as a projection device is known from DE 20 2017 103 902 U1. All of the aforementioned writings have in common that, even in combination, they do not solve the speed problem for the pulsed operation of the headlights. Task To make LiDAR systems better and more reliable, the system's sensitivity must be increased, for example, to extend the range or enable the visibility of dark objects. This can be achieved either through a more sensitive sensor or by increasing the transmission power. Sensors are already operating close to their physical limits, while transmission power is subject to legal restrictions. Therefore, a significant improvement can only be achieved by improving the light source while adhering to the applicable legal limitations. As will be explained below, a key subtask here is to generate short light pulses without slow rise and fall times of the pulse width, which are caused by parasitic effects. The proposed technical solution aims to drastically reduce the rise and fall times of an LED light pulse to generate extremely short pulses (<1 ns). This would allow cost-effective LEDs to be used efficiently and powerfully in applications such as flash LiDAR. Consequently, in various applications, more expensive laser diodes could be replaced by LEDs. Preferably, the proposed device should also be able to transmit data. This problem is solved by a device according to claim 1 and ultimately by a time-of-flight camera with such a device according to claim 5 and methods according to claims 6 to 8. Solution to the task During the development of the proposal, it was recognized that the required significant improvement could only be achieved by improving the light source while taking into account the applicable legal restrictions, and that there were three possibilities: 1. Shortening the pulse duration of the light source; 2. Increasing the aperture of the light source; 3. Using visible light instead of IR light in order to fall within a higher legally regulated intensity limit due to the natural eyelid reflex. By extending the functionality of a headlight to include a LIDAR light source, a necessity can be turned into a virtue. This requires a headlight capable of pulsed operation. By switching from the continuous static operation of state-of-the-art LED headlights to pulsed operation, the functionality of current headlights can be maintained with comparable average power and a sufficient pulse rate, without any visible difference to the human eye. Pulsed light modulation can also be superimposed on a static lighting signal. For the purposes of this disclosure, "headlights" means all lights of a vehicle, in particular all exterior lights of a vehicle. These include, but are not limited to: the front headlights for daytime running lights, the dipped beam, the main beam, the decorative lights, the direction indicators, the brake lights, the reversing lights, the taillights, the fog lights, the rear fog lights, the warning lights and the signal lights (e.g. the blue light of the police or fire brigade, the yellow warning light of heavy transport vehicles, etc.). Since the light sources are located in different positions on the vehicle, an environmental map (EM) can be generated in the immediate vicinity by triangulation. This information can potentially be exchanged with preceding and following vehicles via a data link, which can potentially be established via the proposed light pulse-capable headlight. This achieves the effect of imprinting a time signal on the emitted light, which can then be used for distance measurement. For white headlights, this is possible by using RGB LEDs instead of fluorescent LEDs (LED2...n) as the primary light source, since the latter do not allow for rapid modulation. It is crucial that modulation is possible in at least one spectral range. This can be achieved, for example, by filtering out the light from a fluorescent LED (LED2...n) in a specific spectral range and replacing it with the light from a narrow-wavelength auxiliary LED (LED1), which can then be rapidly modulated. Thus, a rapidly modulatable spotlight (SW) is proposed here, suitable for use in LiDAR applications. This spectral range of the emitted and modulated wavelength can then be separated by an optical bandpass filter (F1) for a receiver (PD1). By using vehicle headlights as a LiDAR light source, a higher overall transmission power can be achieved at the same intensity due to the larger aperture compared to significantly smaller IR light sources. Furthermore, higher intensity limits apply legally in the visible wavelength range, as the natural eyelid reflex acts as a protective mechanism. Therefore, such an optical system operating in the visible wavelength range is superior to a system based on infrared radiation. The challenge here lies in generating short light pulses (LP), particularly with the existing light sources on the vehicle, such as headlights, turn signals, brake lights, taillights, reversing lights, etc., and any additional light sources that may be installed. The aim of the proposed device and method is to generate the shortest possible light pulses (LP) by means of a first LED (LED1) as the light source of such headlights (SW1). The afterglow of the first LED (LED1) after the operating current is switched off, caused by the charges stored in the depletion layer of the first LED (LED1), is now to be avoided by not discharging the charges stored in the depletion layer of the first LED (LED1) by recombination, but by actively removing these charge carriers. To effect this removal, it is proposed to reverse the polarity of the operating voltage of the first LED (LED1). Furthermore, it is proposed to perform this polarity reversal using a proposed H-bridge (H) and a proposed method. To further accelerate the removal of the remaining charge carriers, it is proposed to carry out the actual removal process using a charge pump or a voltage converter, thereby maximizing the electric field strength acting on the charge carriers during the removal process. To increase the steepness of the rising edge, a high voltage must be applied to the first LED (LED1) for a short time. The steepness is directly proportional to the applied voltage. To accelerate the falling edge, the same process must be repeated with reversed polarity until the junction capacitance of the first LED (LED1) has been actively discharged by the driver. An H-bridge (H) provides precisely this control capability. It is important to ensure that the overvoltage is not applied for too long, thus preventing the first LED (LED1) from being overloaded. It was therefore recognized during the development of this proposal that with an H-bridge (H) or a comparable circuit, by briefly applying a positive voltage in the forward direction of the first LED (LED1), followed by a high negative voltage in the reverse direction of the first LED (LED1), the parasitic components of the first LED (LED1) and their connection to the driver are recharged more quickly, which leads to a significantly improved edge steepness and thus enables much shorter pulses.It was also recognized that the charge stored in the parasitic elements of the first LED (LED1) is finite and that the high negative voltage for extracting the stored charge carriers can therefore be supplied by charge pumps with sufficient capacity, which allow an increase in the negative high voltage in the reverse direction of the first LED (LED1), referred to below as the extraction voltage, by several times the operating voltage, i.e. the forward voltage in the forward direction of the first LED (LED1). In a first embodiment of the proposal, a first light-emitting diode (LED1), having a cathode (K) and an anode (A), is driven. The first LED (LED1) is connected via its cathode (K) to the second terminal (2) of the first transistor (T1) and the third terminal (3) of the second transistor (T2), and via its anode (A) to the sixth terminal (6) of the third transistor (T3) and via the seventh terminal (7) of the fourth transistor (T4). The first terminal (1) of the first transistor (T1) and the fifth terminal (5) of the third transistor (T3) are connected to the first positive supply voltage (VCC1). The fourth terminal (4) of the second transistor (T2) and the eighth terminal of the fourth transistor (T4) are connected to the second negative supply voltage (GND2). The first transistor (T1) can assume two operating states: a first operating state and a second operating state.When the first transistor (T1) is in its first operating state, current can flow from the first positive supply voltage (VCC1) to the cathode (K) of the LED (LED1). In the second operating state of the first transistor (T1), the first terminal (1) of the first transistor (T1) has a higher resistance to the second terminal (2) than in the first operating state. In this second operating state, current cannot flow to the cathode (K) of the LED (LED1). The first transistor (T1) enters its first operating state when its first control terminal (G1) is in a first logic state and its second operating state when its first control terminal (G1) is in a second logic state. The second transistor (T2) can assume two operating states: a first operating state and a second operating state. In the first operating state, charge carriers can flow from the third terminal (3) of the second transistor (T2) to the fourth terminal (4). In the second operating state, the third terminal (3) of the second transistor (T2) has a higher resistance to the fourth terminal (4) than the third terminal (3) does to the fourth terminal (4) in the first operating state. In this second operating state, charge carriers essentially cannot flow through the second transistor (T2).The second transistor (T2) assumes the first operating state when its second control terminal (G2) is in a first logic state and the second operating state when its second control terminal (G2) is in a second logic state. The third transistor (T3) can assume two operating states: a first operating state and a second operating state. In the first operating state, charge carriers can flow from the fifth terminal (5) of the third transistor (T3) to the sixth terminal (6) of the third transistor (T3). In the second operating state, the fifth terminal (5) of the second transistor (T2) has a higher resistance to the sixth terminal (6) of the third transistor (T3) than in the first operating state. In this second operating state, charge carriers essentially cannot flow.The third transistor (T3) assumes the first operating state when its third control terminal (G3) is in a first logic state and the second operating state when its third control terminal (G3) is in a second logic state. The fourth transistor (T4) can assume two operating states: a first operating state and a second operating state. In the first operating state, charge carriers can flow from the seventh terminal (7) of the fourth transistor (T4) to the eighth terminal (8). In the second operating state, the seventh terminal (7) is connected to the eighth terminal (8) of the fourth transistor (T4) with a higher resistance than in the first operating state. In this second operating state, charge carriers essentially cannot flow.The fourth transistor (T4) enters the first operating state when its fourth control terminal (G4) is in a first logic state and the second operating state when its fourth control terminal (G4) is in a second logic state. The control terminals (G1, G2, G3, G4) are controlled by a control element (ST). Each of the control terminals (G1, G2, G3, G4) can be in a first logical state or a second logical state. However, it is advantageous if the control terminals (G1, G2, G3, G4) are in one of the following three overall states. In the first overall state, the "PZ" state (PZ), all control connections (G1, G2, G3, G4) are in a second logic state. This means that all transistors (T1, T2, T3, T4) are in their second operating state, and therefore no electrical current can flow and the first LED (LED1) does not emit light. In pulsed operation, the proposed device is preferably in the "PZ" state (PZ). In the second overall state, the "PAn" state (PAn), the second control terminal (G2) and the third control terminal (G3) are in a first logic state, and thus the second transistor (T2) and the third transistor (T3) are in the first operating state. The first control terminal (G1) and the fourth control terminal (G4) are in a second logic state. Thus, the first transistor (T1) and the fourth transistor (T4) are in the second operating state. The first LED (LED1) is forward-biased and emits light. Therefore, the electric current flows from the second positive supply voltage (VCC2) through the third transistor (T3), which is in the first operating state, and the first LED (LED1) and the second transistor (T2), which is in the first operating state, to the first negative supply voltage (GND1).In pulsed operation, the "PAn" state (PAn) is preferably only assumed for a very short time, the turn-on time (tpp). In a third overall state, the "PAus" state (PAus), the second control terminal (G2) and the third control terminal (G3) are in a second logic state, and thus the second transistor (T2) and the third transistor (T3) are in their second operating state. The first control terminal (G1) and the fourth control terminal (G4) are in a first logic state. Thus, the first transistor (T1) and the fourth transistor (T4) are in their first operating state. The first LED (LED1) is energized in reverse with the discharge current and does not emit light.The electrical discharge current now flows to eliminate the charge carriers stored in the first LED (LED1), the second transistor (T2), and the third transistor (T3) immediately after the polarity reversal. It flows from the first positive supply voltage (VCC1) through the first transistor (T1), which is in its initial operating state, and through the first LED (LED1) and the fourth transistor (T4), which is also in its initial operating state, to the second negative supply voltage (GND2). In pulsed operation, the "PAn" state (PAn) is preferably held only for a very short time, the clearing time (τpn). In one proposed variant, the control element (ST) is designed so that a direct transition from the second overall state, the "PAn" state (PAn), to the third overall state, the "PAus" state (PAus), is preferably not possible. The first overall state, the "PZ" state (PZ), must always be entered first to avoid short circuits (see Fig. 2).To remove the charge carriers from the depletion region of the first LED (LED1) according to the proposed method, the system switches as quickly as possible from the second overall state, the "PAn" state (PAn), through the first overall state, the "PZ" state (PZ), to the third overall state, the "PAus" state (PAus). The switching-off process of the first LED (LED1) is described here. At the beginning of the switching-off process, an electric current flows through the first LED (LED1). The system is therefore in the second overall state, the "PAn" state (PAn). Charge carriers are thus stored in the first LED (LED1), and light is emitted from it. Now, at a first time point (t0), the system switches to the first overall state, the "PZ" state (PZ). Since the charge carriers are not removed, they are only dissipated in the first LED (LED1) over a charge carrier lifetime (τ).To accelerate this process, the control unit (ST) initiates a transition from the first overall state, the "PZ" state (PZ), to the third overall state, the "PAus" state (PAus), after a delay time (Δt) that is shorter than the charge carrier lifetime (τ). Due to the polarity reversal and the fact that the delay time (Δt) is shorter than the charge carrier lifetime (τ), the charge carriers stored in the depletion region of the first LED (LED1) are removed more quickly by means of the now possible discharge current through the first transistor (T1) and the fourth transistor (T4). This makes it possible to send shorter light pulses (LP). In accordance with this disclosure, the control element (ST) controls the state of the device such that an increased forward voltage (UDR) is applied to the first LED (LED1) for a very short on-time (τpp). Subsequently, an increased reverse voltage (URM) is applied to the first LED (LED1) for another very short turn-off time (τpn). This turn-off time (τpn) is preferably dimensioned such that a residual charge of the stored charge remains in the first LED (LED1) after the end of the turn-off time (τpn), protecting it from damage by avalanche effects. Advantage of the proposal This offers numerous advantages over current approaches: 1. Ability of spotlights (SP) to emit short light pulses (LP). 2. Increased transmission power due to a larger aperture compared to conventional LiDAR light sources, as spotlights (SP) have a larger radiating surface. 3. Increased transmission power compared to conventional LiDAR light sources through the use of visible light, utilizing the eyelid reflex. 4. Elimination of separate light sources for LiDAR. 5. Higher sensitivity and bandwidth of the receiving photodiodes in the visible wavelength range due to the lower penetration depth of light into silicon or the respective semiconductors. 6. Ideal positioning of the LiDAR light source, as spotlights (SP) are already optimized to illuminate the danger zone. Description of the further education / training courses in the proposal In another proposed method, the light-emitting diode (LED1) is controlled via an H-bridge. The first LED (LED1) is energized in the forward direction in the so-called "PAn" state of the H-bridge (H) until a first time point (t0). After the first time point (t0), the current is reversed at a second time point (t1). That is, from the second time point (t1), the LED (LED1) is energized in the reverse direction in the "PAus" state until all charge carriers are removed and it is reverse-biased. The time difference between a first time point (t0) and a second time point (t1), the delay time (Δt) for remaining in the “PZ” state, in which all transistors (T1, T2, T3, T4) are switched off, when switching from the “PAn” state, in which the first LED (LED1) is forward-biased to the “PAus” state, in which the LED (LED1) is reverse-biased, should again be shorter than the charge carrier lifetime (τ) of the electron-hole pairs in the depletion region of the first LED (LED1). In a further embodiment, the proposed device is supplemented by a positive charge pump (LPPB) (or a positive voltage converter (SVPB)) for the rapid extraction of the stored charge carriers and a negative charge pump (LPMB) (or a negative voltage converter (SVMB)) for the rapid extraction of the stored charge carriers. In the proposed device, the positive charge pump (LPPB) (or the positive voltage converter SVPB) is connected to the positive supply voltage (VCC) via its ninth terminal (9). The negative charge pump (LPMB) (or the negative voltage converter (SVMB)) is connected to the negative supply voltage (GND) via its eleventh terminal (11). The other power supplies for the charge pumps (LPPB, LPMB) and the voltage converters (SVPB, SVMB) are not shown in the figures. The potential of the tenth terminal (10) of the positive charge pump (LPPB) (or the positive voltage converter (SVPB)) is higher than the potential of the twelfth terminal (12) of the negative charge pump (LPMB) (or the negative voltage converter (SMB)). Furthermore, the voltage potential (VCC1) of the positive charge pump (LPPB) (or the positive voltage converter (SVPB)) is preferably higher than that of the positive supply voltage (VCC).The voltage potential (GND2) of the output (12) of the negative charge pump (LPMB) (or negative voltage converter (SVMB)) for the rapid removal of the stored charge carriers is preferably lower than that of the negative supply voltage (GND). The device is supplemented by the charge pumps or voltage converters by connecting a positive charge pump (LPPB) (or positive voltage converter (SVPB)) with its tenth terminal (10) as the first positive supply voltage (VCC1) to the first terminal (1) of the first transistor (T1), and the negative charge pump (LPMB) (or negative voltage converter (SVMB)) for the rapid removal of the stored charge carriers with its twelfth terminal (12) as the second negative supply voltage (GND2) to the eighth terminal (8) of the fourth transistor (T4).This means that the positive second supply voltage (VCC2) is only connected to the fifth terminal of the third transistor (T3), and the negative first supply voltage (GND1) is only connected to the fourth terminal of the second transistor (T2). It is now possible to remove the charge carriers more quickly from the depletion region of the first LED (LED1) by means of a suitable clearing voltage, which can be generated by the output voltages (VCC1, GND2) of charge pumps (LPPA, LPMB) or voltage regulators (SVPA, SVPB). In a further embodiment of the proposed method, the generation of fast light pulses (LP) is proposed by the premature removal of charge carriers from a light-emitting diode (LED) having a cathode (K) and an anode (A). For this purpose, the first LED (LED1) is initially operated in the forward direction until a switch-off time (t0) by applying a first potential difference between the anode (A) and the cathode (K), where this first potential difference is positive with respect to the cathode (K) as the reference potential node. Afterwards, the first LED (LED1) is operated by applying a second potential difference between the anode (A) and the cathode (K) of the first LED (LED1), where this second potential difference is negative with respect to the cathode (K) as the reference potential node. Thus, the first LED (LED1) is operated in reverse bias from the switch-off time (t0). The proposed methodology for generating short light pulses (LP) using light-emitting diodes (LEDs) is particularly suitable for flash LiDAR applications, TOF distance measurement, 3D imaging and optical data link applications. A headlight (SW) for use in vehicles (Kfz) is proposed here, in which the headlight (SW) is equipped with at least one first LED (LED1) as a light source, which can be pulsed. The first LED (LED1) can be a standard LED, a laser diode, or a combination of several such diodes and / or laser diodes. A series connection of several LEDs is particularly preferred. The previously described H-bridge circuit can preferably be used for this pulsing. It may be desirable not to operate all light sources (LEDs) in pulsed mode. This means that, in addition to the pulsed light component, there is a more or less static light component emitted by the headlight (SW). Therefore, in this case, the proposed headlight (SW) can include further light sources (LED2...n) that then emit this static light component. The headlight (SW) should preferably emit light in the visible wavelength range.This wavelength range is referred to below as the emitted wavelength range (EWR). It is proposed that the illuminator (I) be capable of emitting light pulses (LP) in at least one visible wavelength range, the light pulse-capable wavelength range (LPWB), in order to use it as a light source for the aforementioned light pulse-based measurement methods. The light pulse-capable wavelength range (LPWB) should be a subrange of the emitted wavelength range (EWR) of the illuminator (I) or be identical to the emitted wavelength range (EWR) of the illuminator (I). It is therefore conceivable, for example, that the illuminator (I) could be powered by light sources other than the first LED (LED1), which, for example,A fluorescent agent is excited to emit white light, which is not capable of pulsed light emission. A single first LED (LED1) then emits pulsed light in the pulsed wavelength range (LPWB) using the previously described control circuit, for example, in the form of the aforementioned H-bridge (H). The first LED (LED1) should therefore be able to emit pulsed light as a light pulse (LP) in this pulsed wavelength range (LPWB). It is important that this range should be preferentially visible to provoke the eyelid reflex in humans, which further increases the permissible transmission power. This increases the range of LIDAR applications. At least the first LED (LED1) is preferably driven by the previously described H-bridge (H) to generate the most intense light pulses (LP) with the shortest possible duration. Headlight variant 1 An important first variant of the proposed headlight (SW) is equipped with a first optically blocking bandpass filter (F1) in which the blocked wavelength range (GWB) lies within the visible emitted wavelength range (GWB) of the headlight (SW). In this variant, the proposed headlight (SW) is equipped with at least one second LED (LED2) as an additional light source. This second LED (LED2) emits visible light through the first optically blocking bandpass filter (F1), at least in the unblocked wavelength range (NGWB) of the emitted wavelength range (AWB) of the headlight (SW). The first LED (LED1), on the other hand, emits light in the wavelength range (GWB) blocked by the optically blocking bandpass filter (F1) without this light from the first LED (LED1) having to pass through the first optically blocking bandpass filter (F1).This prevents the receiver (MD) and thus the receiving channel from being overloaded due to a high DC component in the emitted light of the headlight (SW) in the blocked wavelength range (GWB). If the blocked wavelength range (GWB) is chosen to be very narrow and the spectral width of the emission from the first LED (LED1) is also narrow, a change in the perceived color of the emitted light from the headlight (SW) can potentially be avoided. Headlight variant 2 In a second embodiment of the proposed headlight (SW), the headlight (SW) comprises at least one first LED (LED1a) emitting in a first wavelength range (WB1), at least one second LED (LED1b) emitting in a second wavelength range (WB2), and at least one third LED (LED1c) emitting in a third wavelength range (WB3). It is particularly preferred that the headlight incorporates an RGB LED as the light source, typically comprising three LEDs as an LED group capable of emitting in three different colors – preferably RGB, i.e., R=red, G=green, and B=blue. These three LEDs then represent the first LED (LED1a), the second LED (LED1b), and the third LED (LED1c). However, in a vehicle headlight (SW) and other applications, the luminous intensity of a single RGB LED is generally insufficient.It is therefore typically the case that a first group of several LEDs capable of emitting in the first wavelength range (WB1) jointly constitutes the first LED (LED1a) as defined in this disclosure, that a second group of several LEDs capable of emitting in the second wavelength range (WB2) jointly constitutes the second LED (LED1b) as defined in this disclosure, and that a third group of several LEDs capable of emitting in the third wavelength range (WB3) jointly constitutes the third LED (LED1c) as defined in this disclosure. The first wavelength range (WB1), the second wavelength range (WB2), and the third wavelength range (WB3) are preferably visible subranges of the emitted wavelength range (AWB) of the illuminator (SW). The first wavelength range (WB1) is not the same as the second wavelength range (WB2).In this context, "equal" means that the wavelength ranges (WB1, WB2) are not identical, but may overlap at least partially. Likewise, the first wavelength range (WB1) is not the same as the third wavelength range (WB3) and the third wavelength range (WB3) is not the same as the second wavelength range (WB2). The first LED (LED1a), the second LED (LED1b), and the third LED (LED1c) can be controlled, as is well known in the art, by suitable PWM control so that their light appears white to a human observer. This is very important for many applications, since, for example, the function of a headlight as a headlight (SW) is to provide information to the driver, e.g., by color-coding or varying the luminous amplitude to indicate objects in the road. This information also includes the color information of objects in the road. Headlight variant 3 The term headlight (SW) is used very broadly in this disclosure. Various headlights already known today could be designed in the form described above. Headlight variant 3.1 For example, in the case of a vehicle, this could include a headlight for daytime running lights, a headlight for low beam, a headlight for high beam, a decorative light, a turn signal, a warning light, a blind spot warning light (typically mounted on the side mirror), a brake light, a reversing light, a taillight, a fog light, a rear fog light, a warning light, a signal light, in particular a police or fire brigade or other emergency vehicle blue light or other yellow warning light with or without rotation and with or without flashing function. This list is not exhaustive, however, so other applications are conceivable. Headlight variant 3.2 For example, in the case of a rail vehicle, this could be a driving light, a decorative light, a warning light, a reversing light, a taillight, a warning light, or a signal light. However, this list is not exhaustive, so other applications are conceivable. Headlight variant 3.3 For example, in the case of a simple luminaire, a spotlight (SW) as described above could be a street light, a searchlight, a stage light or stage spotlight, a signal light (e.g., a railway signal light), a traffic light (e.g., a road traffic light), an emergency light, a workplace light, a room light, a corridor light, or a self-illuminating advertising sign. However, this list is not exhaustive, and further applications in other types of luminaires are expressly conceivable. Headlight variant 4 In another variant of the spotlight (SW), the previously described spotlight serves as the light source for a projection device. Such a projection device could be, for example, a matrix spotlight that uses a segmented LCD display to amplitude-modulate individual sections of the emitted light cone, or a projection device for illuminating buildings, streets, and / or other areas that are to be monitored for the presence of objects and / or people. In this case, it can be useful to mask out certain areas. This is particularly relevant when objects need to be marked. Such a projection device preferably comprises a structurable aperture (LCD). Such a structurable aperture (LCD) consists, for example, of a first polarizing filter, a first transparent electrode layer with spatially resolved electrodes, a liquid crystal layer, a second transparent electrode layer with spatially resolved electrodes (the electrodes of the two electrode layers are opposite each other, and the liquid crystal layer lies between these electrodes), and a second polarizing filter. The array of electrodes and liquid crystals is located between the polarizing filters. The electrodes are electrically insulated but can be kept under voltage by controlling the filter.Depending on the voltage between an electrode of the first electrode layer and an opposing electrode of the second electrode layer, the rotation angle of the polarization plane of the light transmitted through the first polarizing filter in the liquid crystal layer changes, and thus the transmission of this light through the second polarizing filter changes. If already polarized light is emitted by the light source, e.g., the first one (LED1), the first polarizing filter can be omitted. This aperture (LCD), whose transmission for the light from the light source (LED1) can therefore be structured, represents a two-dimensional surface, which, however, does not necessarily have to be flat.It therefore possesses spatially resolved and locally adjustable transmission coefficients for the light emitted by the first LED (LED1) for each two-dimensional sub-area (transparent electrodes) of this two-dimensional surface and relative to the perpendicular to these respective two-dimensional sub-areas. To be able to image the light beam with such spatially varying amplitude modulation, optics (CL, PL) are necessary to project the light pulse (LP) emitted by the light source, e.g., the first LED (LED1), onto a projection surface or into a projection space. The structured aperture (LCD) can then be used to modulate the cross-section of the light beam exiting the spotlight (SW). Individual pixels can also be modulated, which can affect, for example, the color or its temporal modulation (e.g., blinking).If the cross-section of the light beam exiting the headlight (SW) is to be modulated in this manner by means of the aforementioned structured aperture (LCD), it is advantageous for the optics (Cl, PL) to include at least a condenser lens (CL) or an equivalent mirror device. It is also known from the prior art that projection devices can also be implemented using two-dimensional arrays of micromirrors (DLP), i.e., micromirrors (DLP) arranged in the form of a two-dimensional grid. If such micromirror arrays (DLP) are located in the beam path, they can be used for modulation in the same way. Therefore, a structured micromirror array (DLP) can also be considered a structurable aperture (LCD) within the meaning of this disclosure, which spatially resolves partial beams of the light source's beam, e.g., the first LED (LED1), by deflecting or otherwise modulating them from the beam path. The structurable aperture (LCD) can be located in front of, behind and between components of the optics (CL, PL, OP) in the beam path. The headlight (SW) can be configured to selectively highlight objects (O) within its illumination range by means of appropriate lighting, while other areas remain unmarked. For example, pedestrians or objects identified by the system as potentially hazardous could be illuminated in a suitable color, while the remaining objects within the headlight range would be illuminated in white. Furthermore, the headlight (SW) can be configured to selectively highlight such objects (O) within its illumination range by means of a temporal lighting pattern, particularly by flashing and / or by using a different colored light. For example, the aforementioned hazardous objects could be illuminated with a brightness that fluctuates over time according to a predetermined pattern, while other objects (O) remain constantly illuminated. In this way, oncoming drivers, for instance, can be specifically warned.This results in two modulation channels for the light emitted by the headlight: one for vehicle-to-vehicle communication with very short light pulses (LP) that are imperceptible to humans and should not be noticeable to the drivers, and one channel for vehicle-to-driver communication with relatively slow color and / or brightness modulations that are perceptible to humans, where the driver can be the driver of the vehicle or of another vehicle. Headlight variant 5 It is further proposed to install such a headlight (SW) in a vehicle (Kfz). All types of vehicles are eligible: cars, trucks, motorcycles, rail vehicles, bicycles, all types of marine vessels such as ships, boats and submarines, aircraft, spacecraft, special vehicles such as tracked vehicles and construction vehicles and machinery, mobile robots, industrial trucks, etc. This section primarily describes the application in motor vehicles. However, the application is not limited to this. The claim also extends to other vehicles, such as those mentioned above. Such a proposed vehicle (motor vehicle) includes at least one headlight (SW) as previously described. Basic procedure Using the previously described spotlight (SW), light, particularly light pulses (LP), can now be emitted, suitable for use in measuring devices. The basic method involves the emission of a light pulse (LP) or a sequence of light pulses (LPF) by the first LED (LED1). For the purposes of this disclosure, a light pulse (LP) can be either a brief activation or a brief deactivation of the first LED (LED1). In the broadest sense, these are short-term intensity modulations. Thus, positive light pulses can be emitted, in which the first LED (LED1) is activated at a first time (t1) and deactivated again a short time later at a second time (t2).It is therefore also possible to emit negative light pulses (LP), in which the first LED (LED1) is initially switched on, then switched off at a first time (t1), and switched on again after a short time at a second time (t2). Furthermore, it is possible for the light emission of the first LED (LED1) to have a positive equivalent value, to which the light pulses (LP) are superimposed. For the purposes of this disclosure, a light pulse (LP) is thus characterized by the fact that the luminous intensity of the visible light emitted by the first LED (LED1) increases or decreases from a first luminous intensity to a second luminous intensity at a first time (t1) and returns to the first luminous intensity at a second time (t2) following the first time (t1).The time difference between the second time point (t2) minus the first time point (t1) is preferably less than 10µs, better less than 3µs, better less than 2µs, better less than 1µs, better less than 500ns, better less than 200ns, better less than 100ns, better less than 50ns, better less than 20ns, better less than 10ns, better less than 5ns, better less than 4ns . 1. Procedure variant Furthermore, a method for emitting light using the previously described spotlight (SW) is proposed, in which the first LED (LED1a) of the spotlight (SW) emits visible light in a first wavelength range (WB1), and the second LED (LED1b) of the spotlight (SW) emits visible light in a second wavelength range (WB2), which is not the same as the first wavelength range (WB1). A light pulse (LP) or a sequence of light pulses (LPF) is then emitted by the first LED (LED1). The intervals between the light pulses (LP) can be constant or modulated (varying). The intervals between the light pulses (LP) within the sequence of light pulses (LPF) can encode information.A light pulse (LP) within the meaning of this disclosure is characterized in that the luminous intensity of the visible light emitted by the first LED (LED1) increases or decreases from a first luminous intensity to a second luminous intensity at a first time point (t1) and returns to the first luminous intensity at a second time point (t2) following the first time point (t1). The time difference between the second time point (t2) minus the first time point (t1) is preferably less than 10 µs, better less than 3 µs, better less than 2 µs, better less than 1 µs, better less than 500 ns, better less than 200 ns, better less than 100 ns, better less than 50 ns, better less than 20 ns, better less than 10 ns, better less than 5 ns, better less than 4 ns. 2nd procedural variant In a second variant of the method, a method for emitting light using the previously described spotlight (SW) is proposed, in which the first LED (LED1a) of the spotlight (SW) emits visible light in a first wavelength range (WB1) (first color), and the second LED (LED1b) of the spotlight (SW) emits visible light in a second wavelength range (WB2) (second color), which is not the same as the first wavelength range (WB1). In contrast to the first variant, however, the amplitude of the first LED (LED1) is not modulated, but rather the color angle of the emission from the two LEDs (LED1a, LED1b). The sum of the luminous flux emitted by the first LED (LED1a) and the second LED (LED1b) preferably remains constant; only the color angle is changed by altering the relative luminous fluxes of the first LED (LED1b) and the second LED (LED1b).The proposed method therefore involves the emission of a colored-angle light pulse (CLP) or a sequence of colored-angle light pulses (CLPF) by the first LED (LED1a) and the second LED (LED1b). The spacing of the colored-angle light pulses (CLP) can be constant or modulated (varying). The spacing of the colored-angle light pulses (CLP) within the sequence can encode information.A colored angle light pulse (CLP) is characterized in that the luminous flux of the visible light emitted by the first LED (LED1a) increases or decreases from a first luminous flux of the first LED (LED1a) to a second luminous flux of the first LED (LED1a) at a first time (t1) and returns to the first luminous flux of the first LED (LED1a) at a second time (t2) following the first time (t1), and simultaneously and preferably synchronously, the luminous flux of the visible light emitted by the second LED (LED1b) decreases or increases from a first luminous flux of the second LED (LED1b) to a second luminous flux of the second LED (LED1b) at a first time (t1) and returns to the first luminous flux at a second time (t2) following the first time (t1).Provided that synchronicity can actually be achieved, no change in intensity would be measurable, but only a pulsed color change of preferably a few nanoseconds. This has the advantage that the light intensity remains constant. The total luminous flux, from the sum of the luminous flux of the visible light emitted by the second LED (LED1b) and the visible light emitted by the first LED (LED1a), then preferably changes by no more than 10% during the emission of the colored angular pulse (CSP). The time difference between the second time point (t2) minus the first time point (t1) is preferably less than 10µs, better less than 3µs, better less than 2µs, better less than 1µs, better less than 500ns, better less than 200ns, better less than 100ns, better less than 50ns, better less than 20ns, better less than 10ns, better less than 5ns, better less than 4ns . 3. Procedure variant Precise synchronization of the control of the two LEDs, as described in the preceding method variant, cannot be achieved, either in terms of timing or amplitude. Therefore, in reality, a short-term amplitude fluctuation combined with a pulsed color fluctuation is more realistic. A third method variant is therefore proposed, which describes a method for emitting light, particularly combined color / light pulses, using the spotlight (SW) described above. In this method, the first LED (LED1a) of the spotlight (SW) emits visible light in a first wavelength range (WB1), and the second LED (LED1b) of the spotlight (SW) emits visible light in a second wavelength range (WB2), which is not the same as the first wavelength range (WB1).The proposed third method variant involves the emission of a modulated color-angle light pulse (MFLP) or a sequence of modulated color-angle light pulses (FMLPF) by the first LED (LED1a) and the second LED (LED1b). The spacing of the combined modulated color-angle light pulses (FMLP) can be constant or modulated (varying). The spacing of the modulated color-angle light pulses (FMLP) within the color-angle light pulse sequence (FMLPF) can encode information.A modulated color-angle light pulse (MFLP) is characterized in that the luminous intensity of the visible light emitted by the first LED (LED1a) increases or decreases from a first luminous intensity of the first LED (LED1a) to a second luminous intensity of the first LED (LED1a) at a first time (t1) and returns to the first luminous intensity of the first LED (LED1a) at a second time (t2) following the first time (t1), and that the luminous intensity of the visible light emitted by the second LED (LED1b) decreases or increases from a first luminous intensity of the second LED (LED1b) to a second luminous intensity of the second LED (LED1b) at a first time (t1) and returns to the first luminous intensity at a second time (t2) following the first time (t1).The first total luminous flux, calculated as the sum of the first luminous flux of the second LED (LED1b) and the first luminous flux of the first LED (LED1a), and the second total luminous flux, calculated as the sum of the second luminous flux of the second LED (LED1b) and the second luminous flux of the first LED (LED1a), differ, at least at one point in time between the first time (t1) and the second time (t2), preferably by more than 10%. This can be caused, for example, by the light pulses (LP) not starting at exactly the same time, or by having different maximum heights or shapes. Since LEDs of different colors can be used, this can easily occur due to different designs and manufacturing variations.The time difference between the second time point (t2) minus the first time point (t1) is preferably less than 10µs, better less than 3µs, better less than 2µs, better less than 1µs, better less than 500ns, better less than 200ns, better less than 100ns, better less than 50ns, better less than 20ns, better less than 10ns, better less than 5ns, better less than 4ns. 4. Procedure variant The previously described method variants and the basic method can also be used for data transmission. Therefore, a method for transmitting data using light from a previously described spotlight (SW) is proposed. The proposed method involves emitting a sequence of light pulses (LP) (light pulse sequence (LPF)) by the first LED (LED1) or a sequence of colored light pulses (color light pulse sequence (FLPF)), wherein data information is encoded by different time intervals of the light pulses (LP) or color light pulses (FLPF) and / or the frequency spectrum of the intervals of the light pulses (LP) or color light pulses (FLPF), or by different phase relationships of the light pulses (LP) or color light pulses (FLPF) relative to each other, particularly within a light pulse sequence (LPF) or color light pulse sequence (FLPF), or by different light pulse amplitudes of the light pulses (LP) or color angle modulation amplitudes of the color light pulse (FLPF).In the case of a color light pulse as defined in this disclosure, the radiation intensity typically remains essentially constant during the emission of the color light pulse (FLP). The characterization "essentially" here refers to unavoidable deviations from the standard. The total intensity (total luminous power) of a color light pulse (FLP) thus remains constant for the duration of the color light pulse (FLP), and only the color, i.e., the hue angle, is pulsed. The proposed method also includes receiving the light pulses (LP) or color light pulses (FLP) in a receiver and decoding the data information contained therein. Since this is pulsed data transmission using broadband light pulses (LP) or broadband color light pulses (FLP), the spectrum of the light modulation signal superimposed on the emitted light is very broad.Therefore, so-called ultra-wideband algorithms can be very effectively used to efficiently reduce the influence of interference signals with a high suppression rate. For example, the received signal can be convolved with a prototype of an expected transmitted pulse sequence, which highlights components in the received signal that correlate with this expected transmitted pulse sequence. It is also possible, for instance, to generate a scalar product between the received signal and such a prototype signal by multiplying the two signals and then applying a low-pass filter to achieve an improved signal-to-noise ratio. Due to the proposed control method, it becomes possible to reliably separate the light pulses (LP) or colored light pulses (FLP) from the noise background, particularly during the reception of these light pulses (LP) after their reflection as reflected light pulses (RLP), using a spread-spectrum method. This allows data transmission over long distances, provided photons can reach the receiver (MD) from the transmitter (LED1). This fourth method variant proposes that data transmission occurs via the light of a headlight (SW), as described above. The headlight (SW) is part of a vehicle (Kfz). The proposed fourth method variant includes, among other things, providing vehicle status information as data to be transmitted before the first LED (LED1) emits a sequence of light pulses (LPF). For example, it is conceivable to display the direction and speed externally using the headlights, e.g.,to transmit information to vehicles ahead or to signal braking maneuvers, including their intensity and speed, to following vehicles via the brake lights. Other information can also be exchanged in this way. As a further sub-variant of the method, the state of traffic infrastructure devices can be changed depending on the received and decoded data information. For example, it is conceivable that control tasks within smart home applications, such as opening garage doors or switching lights on and off, etc., could be controlled. It is also conceivable that infrastructure devices, such as traffic lights, could be controlled. A particularly preferred approach is to connect the vehicle to the internet, whereby the vehicle sends data using its headlights (as defined in this disclosure) (SW), and the traffic infrastructure sends data back, for example, via streetlights. As a further sub-variant of the method, a change in the state of another vehicle can be provided for, depending on the received and decoded data information. Such a change in state can, for example, involve influencing a device in the other vehicle, in particular an optical and / or acoustic display, e.g., for the driver of the second vehicle, and / or a change in important state parameters such as speed and direction, or in the shape of the light beams of the headlights of the second vehicle. A method for transmitting data using the light of a spotlight (SW) is also proposed, where the spotlight (SW) is part of a luminaire. After the data information to be transmitted is provided, prior to the emission of a sequence of light pulses (LPF) by the first LED (LED1), a sequence of light pulses (LPF) is emitted, the data information to be transmitted being encoded within the sequence of light pulses (LPF). In a further variant, the sequence of light pulses (LPF) is then received by a corresponding device of a second luminaire, and the data information to be transmitted, encoded within the sequence of light pulses (LPF), is decoded to obtain the received and decoded data information. The state of the second luminaire or a device connected to it is then changed by its control system depending on the received and decoded data information. In general terms, a method for data transmission to a headlight (SW) can therefore be proposed, in which the headlight (SW) has at least one first LED (LED1) as a light source, and the first LED (LED1) is not energized and therefore does not illuminate, at least during certain periods, the dark periods. During these dark periods, the first LED (LED1) can then be used as a receiver (MD). This can be, for example, the receiver (MD) of a distance measuring device in conjunction with another headlight (SW) of the proposed type. The data transmission method then comprises the steps of detecting at least one light source voltage (VLED1) at the at least one LED (LED1) during a dark period using an H-bridge control instrument (HCV) to measure the voltage drop (VLED1) across the load (LED1) in the H-bridge (H), i.e., typically across the first LED (LED1).The value thus determined can be amplified and appropriately filtered, and then compared with a threshold value (SCHW). If the voltage drop level (VLED1) after appropriate filtering is above the threshold value (SCHW), a first logical state can be generated. If the voltage drop level (VLED1) is below the threshold value (SCHW), a second logical state can be generated. The timing of the first and second logical states can then be used to infer data and / or an underlying data clock signal by an evaluation circuit. In this context, it should be noted that the parasitic capacitances of LEDs used for illumination are generally so large that the actual data rates are very low. However, this can be useful for maintenance purposes. Thus, data is generated here depending on the detected LED voltage (VLED1). 5. Procedure variant As a fifth method variant, a method for determining the distance (d) between an object (O) and a vehicle (Kfz) is proposed. This fifth method variant comprises the emission of a light pulse (LP) by means of a headlight (SW), as described above, into the exterior of a vehicle (Kfz), the reflection of the emitted light pulse (ELP) from an object (O) as a reflected light pulse (RLP), and the reception of the reflected light pulse (RLP) by a receiver (EM) that is part of the vehicle (Kfz). This is followed by the determination of the time-of-flight (TOF) and the calculation of the distance (d) between the object (O) and the vehicle (Kfz) by a computational device (BV) inside the vehicle (Kfz). Various light pulse-based techniques for determining such time-of-flights are known from the prior art (e.g., EP 2 783 232 B1).The disclosure presented here focuses on optimizing light pulse generation and the resulting new applications. Instead of emitting light into the exterior of a vehicle, it is also possible to emit it into the interior of a vehicle using various interior lights, for example, for interior monitoring, seat occupancy detection, etc. It should also be mentioned that, instead of distance measurement, the detection of aerosols, such as fog, becomes possible. For example, a separate optical system can analyze the scattered light from a proposed headlight. In particular, the scattered light from the light pulses (LP) emitted by the proposed headlight then enables the detection of foggy conditions. For this purpose, the measuring device (MV, MD) of Fig. 27 is mounted at a distance from the proposed headlight (SW). The optics (OP3) of the measuring device (MV, MD) are aligned so that their optical axis is not parallel to the optical axis (OP) of the light source (LED1), such that the optical axis of the optics (OP3) of the measuring device (MV, MD) intersects the optical axis of the optics (OP) of the light source (LED1) at a point a distance from the vehicle. An average distance is then measured. If this distance falls below a minimum value, or if the amplitude of the scattered light pulses (LP) from the proposed headlight (SW), which reach the measuring device (MV, MD) from the optical axis of the optics (OP) of the light source (LED1) by scattering, exceeds a maximum value, a fog alarm can be triggered. 6. Procedure variant As a sixth method variant, a method for determining a distance (d) between an object (O) and a vehicle (Kfz) is proposed, in which, in addition to the light travel time of the emitted light pulse (LP), the received amplitude is also evaluated in contrast to method variant 5, and the reflectivity of the reflecting object (O) is also taken into account. This is, for example, a method for determining the reflectivity of an object (O) within the illumination range of a proposed headlight (SW). The method begins with the emission of a light pulse (LP) by a proposed pulse-emitting headlight (SW) into the exterior of a vehicle (Kfz). After the emitted light pulse (ELP) is reflected by the object (O) as a reflected light pulse (RLP), the reflected light pulse (RLP) is received by a receiver (EM) that is part of the vehicle (Kfz). Finally, the reflectivity (REF) of the object (O) is determined by a computational device (BV) inside the vehicle (Kfz). Since distance measurement is possible in this way, the distances (d) thus determined can be further processed. This reflectivity can also be determined spectrally selectively. In this case, it is a method for determining the spectrally selective reflectivity of an object (O) in the illumination range of a headlight (SW). The method begins with the emission of a colored light pulse (CLP) by means of a proposed colored light pulse-capable headlight (SW) into the exterior of a vehicle (Kfz). The emitted colored light pulse consists of a first partial light pulse of a first color and a second partial light pulse of a second color, typically emitted by a first LED (LED1a) and a second LED (LED1b). The total intensity (total luminous flux) of the partial light pulses preferably remains essentially constant for the duration of the colored light pulse (CLP). Preferably, essentially only the color, i.e., for example, the hue, is pulsed.After the emitted colored light pulse (FLP) is reflected by the object (O) as a reflected colored light pulse (RELP), a first reflected partial light pulse (reflecting the first partial light pulse) and a second reflected partial light pulse (reflecting the second partial light pulse) return to the vehicle. Upon reflection from the object, the first and second partial light pulses are reflected with different intensities due to their different colors, as the object's reflectivity differs for these colors. The object is therefore typically colored. The reflected colored light pulse (RFLP), composed of these reflected partial light pulses, is then received by a receiver (EM) located within the vehicle (Kfz). A computational device (BV) within the vehicle then determines the spectral reflectivity (SREF) of the object (O) from the reflectivity measurements of the partial light pulses. 7. Procedure variantA seventh variant of the method proposes a procedure for determining a two-dimensional environmental map (EM) for a vehicle. This involves determining a first distance (d1) to an object (O) using a first headlight (SW1) according to the fifth or sixth variant, and determining a second distance (d2) to an object (O) using a second headlight (SW2) according to the fifth or sixth variant. The environmental map (EM) can contain reflectivities and distances. If more than one color is pulsed, the environmental map can also include spectral values. A two-dimensional position is then calculated according to the coordinate system of the vehicle's environmental map (EM) by transforming the first distance (d1) and the second distance (d2). If further parameters are desired (e.g., reflection, possibly broken down by different colors), these are also calculated here. 8. Procedure variant Therefore, an eighth method variant proposes a procedure for determining a three-dimensional environmental map (EM) for a vehicle. It comprises determining a first distance (d1) to an object (O) using a first headlight (SW1) according to the fifth method variant, determining a second distance (d2) to an object (O) using a second headlight (SW2) according to the fifth method variant, and determining a third distance (d2) to an object (O) using a third headlight (SW3) according to the fifth method variant. For a three-dimensional environmental map to be created, the first headlight (SW1), the second headlight (SW2), and the third headlight (SW3) should not be aligned. The environmental map (EM) can include reflectivities and distances. If more than one color is emitted in pulses, the environmental map (EM) can also include spectral values.The calculation of a three-dimensional position according to the coordinate system of the vehicle's three-dimensional environment map (UDM) is performed by transforming the coordinates from the first distance (d1), the second distance (d2), and the third distance (d3). If further parameters are required (e.g., reflection, possibly broken down by different colors), these are also calculated here. The data from such an environmental map can be used, for example, to determine the distance between the vehicle (Kfz) and a roadway (FB) based on several determined three-dimensional positions within the environmental map (UK). Naturally, other vehicles may also be part of such an environment map (UK). Therefore, a distance between vehicle 1 and another vehicle 2 can be determined based on several calculated three-dimensional positions within the environment map (UK). The proposed principle can also be used to construct a camera in which not only brightness information but also distance information is determined for each pixel. Such cameras are referred to below as TOF camera systems. Similar TOF camera systems are known from the prior art, for example, from DE 10 2008 018 718 B4 and DE 10 2009 020 218 B3 and the publications citing them forwards and backwards. Such a TOF camera system comprises a camera optic (OP3) that generates an image based on the waveform of the returning reflected light pulse (LP). The core of such a TOF camera system is an image sensor that can be switched between light-sensitive and light-insensitive for short periods by the control unit (ST) using a synchronization signal (sync). This image sensor is typically implemented as a two-dimensional array of time-controlled light-sensitive sensors (TOFIMG).A measuring device (MV) evaluates the signals from the two-dimensional arrangement of time-controlled light-sensitive sensors (TOFIMG) and generates a brightness and a time-of-flight image from the acquired data. It is proposed to combine the device described above with the proposed illuminator (SW) to achieve a greater range than is possible with the prior art. The proposed TOF camera system therefore includes at least one LED (LED1) as a light source. The illuminator (SW) of the TOF camera system can include additional light sources, for example, to emit light for illumination purposes. Preferably, however, it is the RGB illuminator (SW) already described, which can thus be configured to emit light and color pulses. To achieve the greater range, the illuminator (SW) emits light in a specific wavelength range (AWB) within the visible wavelength range.This allows the eyelid reflex to be used, increasing the emission power and thus the range. The illuminator (SW) of the TOF camera system is preferably capable of emitting light pulses in at least one visible wavelength range, the light pulsed wavelength range (LPWB). The light pulsed wavelength range (LPWB) is preferably a subrange of the emitted wavelength range (AWB) of the illuminator (SW) or identical to the emitted wavelength range (AWB) of the illuminator (SW). Of course, the illuminator can also emit light in ranges other than the visible wavelength range. This applies to the entire disclosure, but will not be discussed further here. The first LED (LED1) can emit light in this light pulsed wavelength range (LPWB).A control unit (ST) controls the light sensitivity of the controllable light-sensitive sensors (TOFIMG) of the two-dimensional arrangement of time-controlled light-sensitive sensors (TOFIMG) and the emission of light pulses (LP) by the first light source (LED1) to enable time-of-flight measurement on this matrix using the two-dimensional arrangement of time-controlled light-sensitive sensors (TOFIMG). Simultaneously, the headlight (SW) can emit light for illumination purposes. Preferably, the first light source (LED1) is controlled by the proposed H-bridge (H) for controlling and supplying the first LED (LED1) with electrical energy. The H-bridge (H) is preferably controlled by the control unit (ST).Preferably, the TOF camera system includes an optically blocking bandpass filter (F1), wherein the wavelength range blocked by the optical bandpass filter (F1) lies within the visible emitted wavelength range (AWB) of the illuminator (SW). Preferably, the proposed TOF camera system can include at least one second LED (LED2) as an additional light source of the illuminator (SW), which emits visible light (SL) through the optically blocking bandpass filter (F1) at least in the unblocked wavelength range (NGWB) of the emitted wavelength range (AWB) of the illuminator (SW), and wherein the first LED (LED1) emits light in the wavelength range (GWB) blocked by the optically blocking bandpass filter (F1) without this light from the first LED (LED1) having to pass through the optically blocking bandpass filter (F1). It is now advantageous to install such a TOF camera system in a vehicle (car). Preferably, the illuminator (SW) of the TOF camera system is an RGB illuminator. The illuminator (SW) of the TOF camera system then has at least one first LED (LED1) emitting in a first wavelength range (WB1), at least one second LED (LED2) emitting in a second wavelength range (WB2), and at least one third LED (LED3) emitting in a third wavelength range (WB3). As before, the first wavelength range (WB1), the second wavelength range (WB2), and the third wavelength range (WB3) are each a sub-range of the emitted wavelength range (AWB) of the illuminator (SW) of the TOF camera system. The first wavelength range (WB1) is not equal to the second wavelength range (WB2), and the first wavelength range (WB1) is not equal to the third wavelength range (WB3), and the third wavelength range (WB3) is not equal to the second wavelength range (WB2).The control unit (ST) allows the first LED (LED1), the second LED (LED2), and the third LED (LED3) to be preferentially controlled so that their light appears white to a human observer. Of course, a illuminator (SW) of such a TOF camera system can also have only two LEDs. However, a white light impression cannot usually be achieved in this case. The advantage of a TOF camera system with at least two differently colored LEDs is that the first LED (LED1) and the second LED (LED2) can be controlled in such a way that the illuminator (SW) of the TOF camera system is capable of emitting color angle pulses (FLP). This makes it possible to generate time-of-flight images not based on the light travel time of the amplitude, but on the light travel time of a color angle pulse (FLP), which is a completely different method than the methods known in the prior art. It is therefore particularly advantageous if the determination of distance information uses the travel time of a color angle pulse (and possibly not an amplitude pulse). It is particularly advantageous if certain areas identified as critical (e.g., oncoming vehicles) can be protected from the light pulses (LP) and colored light pulses (FLP) under specific conditions. For this purpose, it is necessary to be able to operate the headlight (SW) of the TOF camera system as a projection device, using, for example, an LCD shadow mask to mask the areas to be protected. For this, the TOF camera system preferably again features a structurable aperture (LCD), which preferably represents a two-dimensional surface. This surface has spatially resolved and locally adjustable transmission coefficients for the respective two-dimensional sub-areas of the light emitted by the first LED (LED1a) and, if applicable, the second LED (1b), relative to the perpendicular to these respective two-dimensional sub-areas. Furthermore, a projection optic (CL, PL) is required for projecting the light pulse (LP) or colored light pulse (FLP).Color light pulses (FLP) onto a projection surface or into a projection room are necessary. In contrast to the prior art, the proposed TOF camera system is designed to also function as an illumination device. In this respect, it is advantageous for the TOF camera system to be configured to selectively mark objects within its illumination range, for example, by using the aforementioned shadow mask. This marking can also be temporally modulated. Preferably, the TOF camera system is therefore configured to selectively mark objects within its illumination range by means of a temporal illumination pattern, in particular by flashing and / or by using different colored illumination. List of characters Fig. 1 schematically shows a device in the form of a first exemplary H-bridge (H) that drives or switches off the light source, the first LED (LED1). Fig. 2 schematically shows a device in the form of a first exemplary H-bridge (H) that drives or switches off the light source, the first LED (LED1), with a positive charge pump (LPPB) and a negative charge pump (LPMB) for extracting the stored charge carriers. Fig. 3 schematically shows a device in the form of a first exemplary H-bridge (H) that drives or switches off the light source, the first LED (LED1), with a positive charge pump (LPPB) and a negative charge pump (LPMB) for extracting the stored charge carriers and with a positive charge pump (LPPA) and a negative charge pump (LPMA) for generating a short switch-on edge. Fig. 4 schematically shows a device in the form of a first exemplary H-bridge (H) that drives the light source,The first LED (LED1) is driven or switched off by a pair consisting of a positive charge pump (LPPA) and a negative charge pump (LPMA) to generate a short turn-on edge. Fig. 5 schematically shows a device in the form of a first exemplary H-bridge (H) that drives or switches off the light source, the first LED (LED1), with a positive charge pump (LPPA) to generate a short turn-on edge. Fig. 6 schematically shows a device in the form of a first exemplary H-bridge (H) that drives or switches off the light source, the first LED (LED1), with a negative charge pump (LPMA) to generate a short turn-on edge. Fig. 7 schematically shows a device in the form of a first exemplary H-bridge (H) that drives or switches off the light source, the first LED (LED1), with a negative charge pump (LPMB) for extracting the stored charge carriers. Fig. 8 schematically shows a device in the form of a first exemplary H-bridge (H),The first LED (LED1) drives or switches off the light source using a positive charge pump (LPPB) to extract the stored charge carriers. Fig. 9 schematically shows how a transition from one operating state of the first H-bridge (H) to the next operating state of the first H-bridge (H) is possible. Fig. 10 shows the current waveform for the proposed pulsation method (a) and for alternative prior art control techniques (b, c). Fig. 11 shows the current waveform for the proposed pulsation method (and the voltage waveform across the first LED (LED1)). Fig. 12 corresponds to Fig. 3 with the difference that an H-bridge control instrument (HCV) is additionally provided for measuring the voltage drop across the load in the first H-bridge (H), i.e., typically the light source voltage (VLED1) across the first LED (LED1).to be able to monitor the functionality of the control by the first H-bridge (H) and the first LED (LED1) of the H-bridge (H) during operation. Fig. 13 corresponds to Fig. 12 with the difference that a first H-bridge control instrument (HCI1) is provided for measuring the current through the first switching element of the H-bridge, i.e., typically through the first transistor (T1), here by detecting the voltage drop across the first transistor (T1); a second H-bridge control instrument (HCI2) is provided for measuring the current through the second switching element of the H-bridge, i.e., typically through the second transistor (T2), here by detecting the voltage drop across the second transistor (T2); and a fourth H-bridge control instrument (HCI3) is provided for measuring the current through the third switching element of the H-bridge, i.e., typically through the third transistor (T3), here by detecting the voltage drop across the third transistor (T3).A fourth H-bridge control instrument (HCI4) is provided for measuring the current through the fourth switching element of the H-bridge, typically the fourth transistor (T4), here by detecting the voltage drop across the fourth transistor (T4), and to be able to monitor the functionality of the control by the first H-bridge (H) and the first LED (LED1) of the H-bridge (H) during operation, in particular by inferring the current flow. Fig. 14, like Fig. 9, schematically shows how a transition from one operating state to the next is possible. However, it is now assumed that a different cross-current is desired during the transition from the "PAn" state to the "PAus" state than during the transition from the "PAus" state to the "PAn" state. (See also the description of Fig. 12.) Fig. 15 shows a proposed headlight system schematically simplified and functionally symbolic, where the light source,The first LED (LED1) can be used both in pulsed operation (GPB) and as a light source for quasi-continuous illumination (QDB). Fig. 16 shows an exemplary modified H-bridge (H) for use in a device according to Fig. 15 and in modification of Fig. 3. In contrast to the H-bridge (H) of Fig. 3, the H-bridge (H) of Fig. 16 and the first LED (LED1) can now be used both for the emission of optimized light pulses (LP) and for optimized light emission for illumination purposes by switching between charge pump (LPPA, LPPB, LPMA, LPMB)-based power supply and direct power supply from the supply voltage sources (VCC1, VCC2, VCC3, GND1, GND2). Fig. 17 corresponds to Fig. 16 with the difference that the charge pumps (LPPB, LPPA, LPMA,LPMB) are supplied from a fifth positive supply voltage (VCC5) and a fifth negative supply voltage (GND5), and for operation as a light source in a lighting device, the supply is provided directly from a sixth supply voltage source (VCC6) and a sixth negative supply voltage (GND6), wherein the fifth positive supply voltage (VCC5), the sixth positive supply voltage (VCC6), the fifth negative supply voltage (GND5), and the sixth negative supply voltage (GND6) are preferably outputs of a regulated voltage source. Fig. 18 shows an exemplary modified H-bridge (H) for use in a device according to Fig. 15 and in modification of Fig. 3. In contrast to the H-bridge of Fig. 3, the H-bridge (H) of Fig. 18 and the first LED (LED1) can now be used both for the emission of optimized light pulses (LP) and for optimized light emission for lighting purposes.by using two analog multiplexers to switch between the direct power supply from a third positive supply voltage source (VCC3) and a fourth positive supply voltage source (VCC4) for quasi-continuous operation (QDB) of the first LED (LED1) as the light source of a lighting device, on the one hand, and the direct power supply from a first positive supply voltage source (VCC1) and a second positive supply voltage source (VCC2) for pulsed operation (GPB) as a pulsed LED (LED1), on the other hand. Fig. 19 shows the simplest variant with a supply from a common voltage source with a positive basic supply voltage (VCC).which could, for example, be the power supply from the electrical system of a motor vehicle. In pulsed operation (GPB), the power supply is provided via a common second positive supply voltage (VCC2) and the common negative ground supply voltage (GND). In quasi-continuous operation (QDB), the first LED (LED1) is powered via the third positive supply voltage (VCC3) and the common negative ground supply voltage (GND). Fig. 20 corresponds to Fig. 19 with the difference that the eighth transistor (T8) has been omitted. The analog multiplexer for switching the supply voltage between the second supply voltage (VCC2) and the third supply voltage (VCC3) is therefore no longer mounted on the H-bridge (H) as in Fig. 19.but, by means of the parallel arrangement of the twelfth transistor (T12) with the third transistor (T3), it becomes part of the H-bridge (H). In pulsed operation (GPB), the power supply is provided via a common second positive supply voltage (VCC2) and the common negative ground supply voltage (GND). In quasi-continuous operation (QDB), the first LED (LED1) is powered via the third positive supply voltage (VCC3) and the common negative ground supply voltage (GND). Fig. 21 shows a particularly simple variant of the proposed device. The light source, the first LED (LED1), is supplied with electrical energy by means of an H-bridge (H) consisting of a first half-bridge (HB1: T1, T2) and a second half-bridge (HB2: T3, T4). Fig. 22 corresponds to the state diagram of Fig. 9.The state diagram has now been modified for the operation of the exemplary modified H-bridge (H) of Figs. 16 and 21. Fig. 23 corresponds to Fig. 20 except that two shunt resistors, a first shunt resistor (Rs1) and a second shunt resistor (Rs2), are shown. These shunt resistors (Rs1, Rs2) can be used to determine the current through the respective half-bridge (HB1, HB2) of the H-bridge (H) by measuring the voltage drop across them. Fig. 24 corresponds to Fig. 15 with the exemplary difference that an internal structure of the H-bridge corresponds, for example, to Fig. 15, and where the energy reserves (C_LPPB, C_LPPA, C_LPMB, C_LPMA) of the charge pumps (LPPB, LPPA, LPMB, LPMA) are shown by way of example. Instead of the charge pumps (LPPB, LPPA, LPMB, LPMA), voltage converters (SVPB, SVPA, SVMB,SVMA). In this case, the energy reserves can also be inductors (L_SVPB, L_SVPA, L_SVMB, L_SVMA) or similar. Fig. 25 corresponds to Fig. 13 with the exemplary difference that, for example, a first H-bridge control unit (HC1) is provided, which measures the light emission of the light source, here the exemplary first LED (LED1), by means of a light-sensitive sensor, here for example a first photodiode (PD1), and thus enables readjustment of the control, in particular by adjusting the charge pump voltage of the charge pumps (LPPB, LPPA, LPMB, LPMA) in the form of the output voltage of the energy reserves (C_LPPB, C_LPPA, C_LPMB, C_LPMA) of the charge pumps (LPPB, LPPA, LPMB, LPMA) and by varying the dwell times in the states "PAn", "PAus" and "PZ". Fig. 26 corresponds to Fig. 25 with the exemplary difference that, by way of example, further light sources (LED2...n) are provided,which emit light unpulsed for illumination purposes, wherein a wavelength range, the blocked wavelength range (GWB), is blocked by a filter (F1). Fig. 27 corresponds to Fig. 26, except that a measuring device (MV) is now shown for clarification, which allows, for example, the determination of the light transit time or other information from the reflected light pulses (RLP). Fig. 28 corresponds to Fig. 27 with the difference that a compensation transmitter (K) is now provided, which is driven complementarily to the first LED (LED1), whereby a more or less uniform illumination of the photodiode (MD) is achieved by controlling the amplitude and phase of the drive signal to the compensation diode (K). Fig. 29 corresponds to Fig. 15 with the exemplary difference that, by way of example, a first LED (LED1a), which is driven by an exemplary first H-bridge (H), and a second LED (LED1b) are shown.which is controlled by an exemplary second H-bridge (H'), which opens up the possibility of emitting colored light pulses (FLP). Fig. 30 corresponds to Fig. 15 with the exemplary difference that it is a proposed RGB spotlight (SW) and that, by way of example, a first LED (LED1a) controlled by an exemplary first H-bridge (H), a second LED (LED1b) controlled by an exemplary second H-bridge (H'), and a third LED (LED1c) controlled by an exemplary third H-bridge (H'') are provided, which opens up the possibility of emitting colored light pulses (FLP) and the simultaneous emission of RGB color-defined light, for example also white light, for illumination purposes in the entire RGB color space. Fig. 31 corresponds to Fig. 25 with the exemplary difference that an exemplary, structurable filter, here in the form of an LCD filter (LCD),Fig. 32 is inserted into the beam path, for example, within the optics (CL, PL), and is projected. Fig. 32 corresponds to Fig. 25 with the exemplary difference that an exemplary micromirror array (DLP), here in the form of an LCD filter, is inserted into the beam path and spatially and / or temporally modulates the light beam cross-section. Fig. 33 corresponds to Fig. 25 with the exemplary difference that an exemplary structurable filter (F1), here in the form of an LCD filter (LCD), is inserted into the beam path, for example, behind the optics (OP), and is projected as a shadow mask. Fig. 34 shows exemplary positions of devices according to this proposal on an exemplary motor vehicle (Kfz) in the form of an exemplary passenger car. Fig. 35 shows an exemplary communication between a vehicle (Kfz) equipped with a proposed headlight (SW) and a traffic infrastructure device.Here, an example of a traffic light (AMP) is shown. Fig. 36 shows an example of communication between a first vehicle (Kfz) and a second vehicle (Kfz2), each equipped with a proposed headlight (SW), whereby they use these headlights (SW) to a) actively and a2) passively determine the distances between each other and b) exchange data. Fig. 37 shows the H-bridge from Fig. 1.where the first positive supply voltage (VCC1) of the H-bridge of Fig. 1 and the second positive supply voltage (VCC2) of the H-bridge of Fig. 1 are equal to the total positive supply voltage (VCC), and where the first negative supply voltage (GND1) of the H-bridge of Fig. 1 and the second negative supply voltage (GND2) of the H-bridge of Fig. 1 are equal to the total negative supply voltage (GND). Fig. 38 shows the actual H-bridge (H) with the first half-bridge (HB1) consisting of the series connection of the first transistor (T1) and the series connection of the second transistor (T2), and with the second half-bridge (HB2) consisting of the series connection of the third transistor (T3) and the series connection of the fourth transistor (T4). Fig. 39 corresponds to Fig. 27 with the difference thatthat instead of a single sensor (MD), a two-dimensional arrangement of time-controlled light-sensitive sensors (TOFIMG) is now used for the detection of light pulses (LP) or colored light pulses (FLP). Description of the characters Figure 1 Fig. 1 schematically shows a device corresponding to the previously described H-bridge design. The drawing depicts four transistors (T1, T2, T3, T4), each with three terminals. The first transistor (T1) has a first terminal (1), a second terminal (2), and a first control terminal (G1). The second transistor (T2) has a third terminal (3), a fourth terminal (4), and a second control terminal (G2). The third transistor (T3) has a fifth terminal (5), a sixth terminal (6), and a third control terminal (G3). The fourth transistor (T4) has a seventh terminal (7), an eighth terminal (8), and a fourth control terminal (G4). Each control terminal (G1, G2, G3, G4) is connected to the control element (ST). The control element (ST) controls the logic states of the control terminals (G1, G2, G3, G4).Each control terminal (G1, G2, G3, G4) can be in either a first or a second logic state. The logic state of the control terminal (G1, G2, G3, G4) determines whether the transistor (T1, T2, T3, T4) assumes a first or a second operating state.In a first "PAus" overall state, either the first control terminal (G1) and the fourth control terminal (G4) should be in a first logical state and the second control terminal (G2) and the third control terminal (G3) in a second logical state, and thus the first transistor (T1) and fourth transistor (T4) in a first operating state in which they conduct, and the second transistor (T2) and third transistor (T3) in a second operating state in which they block, or the second control terminal (G2) and the third control terminal (G3) should be in a first logical state and the first control terminal (G1) and the fourth control terminal (G4) in a second logical state, and thus the second transistor (T2) and third transistor (T3) in a first operating state in which they conduct, and the first transistor (T1) and fourth transistor (T4) in a second operating state in which they block.This is the overall "PAn" state. All control terminals (G1, G2, G3, G4) can also be in a second logic state, which places all transistors (T1, T2, T3, T4) in a second operating state where they are off. This is the overall "PZ" state. The LED (LED1) has a cathode (K) and an anode (A). The cathode is connected to the second terminal (2) of the first transistor (T1) and to the third terminal (3) of the second transistor (T2). The anode is connected to the sixth terminal (6) of the third transistor (T3) and to the seventh terminal (7) of the fourth transistor (T4). The LED (LED1) illuminates when the first control terminal (G1) and the fourth control terminal (G4) are in a first logic state and the third control terminal (G3) is in a second logic state.If the second control terminal (G2) and the third control terminal (G3) are in a first logic state, and the first control terminal (G1) and the fourth control terminal (G4) are in a second logic state, the depletion region of the LED (LED1) is cleared by the polarity reversal. Figure 1 also shows a first positive supply voltage (VCC1) and a second positive supply voltage (VCC2), as well as a first negative supply voltage (GND1) and a second negative supply voltage (GND2). The first positive supply voltage (VCC1) is connected to the first terminal (1) of the first transistor (T1). The second positive supply voltage (VCC2) is connected to the fifth terminal (5) of the third transistor (T2). The first negative supply voltage (GND1) is connected to the fourth terminal (4) of the second transistor (T2). The second negative supply voltage (GND2) is connected to the eighth terminal (8) of the fourth transistor (T4). Figure 2 Fig. 2 schematically shows a device corresponding to Fig. 3, but now with a positive and a negative charge pump. The positive charge pump (LPPB) for the rapid removal of stored charge carriers is connected via its tenth terminal (10) to the first terminal (1) of the first transistor (T1). The positive charge pump (LPPB) for the rapid removal of stored charge carriers is also connected via its ninth terminal (9) to a reference potential; in this diagram, the total positive supply voltage (VCC) is shown as the reference potential for the positive charge pump (LPPB) for the rapid removal of stored charge carriers. The negative charge pump (LPMB) for the rapid removal of stored charge carriers is connected via its twelfth terminal (12) to the eighth terminal (8) of the fourth transistor (T4).The negative charge pump (LPMB) for the rapid extraction of the stored charge carriers is also connected to a reference potential via its eleventh terminal (11); in this drawing, the negative total supply voltage (GND) is shown as the reference potential of the negative charge pump (LPMB).The depletion region of the LED (LED1) is cleared more quickly because the potential of the tenth terminal (10) of the positive charge pump (LPPB) for the rapid removal of stored charge carriers is higher than the potential of the twelfth terminal (12) of the negative charge pump (LPMB), and because the voltage potential of the tenth terminal (10) of the positive charge pump (LPPB) for the rapid removal of stored charge carriers is higher than that of the positive supply voltage (VCC), and the voltage potential of the twelfth terminal (12) of the negative charge pump (LPMB) for the rapid removal of stored charge carriers is lower than that of the negative supply voltage (GND). All other sub-devices and processes proceed analogously to Fig. 1. Figure 3 Fig. 3 schematically shows a device corresponding to Fig. 1, but now with a pair of a positive and a negative charge pump for extracting the stored charge carriers and for generating a short switching edge. The positive charge pump (LPPB) for the rapid removal of stored charge carriers is connected via its tenth terminal (10) to the first terminal (1) of the first transistor (T1). The positive charge pump (LPPB) for the rapid removal of stored charge carriers is also connected via its ninth terminal (9) to a reference potential; in this diagram, the total positive supply voltage (VCC) is shown as the reference potential for the positive charge pump (LPPB) for the rapid removal of stored charge carriers. The negative charge pump (LPMB) for the rapid removal of stored charge carriers is connected via its twelfth terminal (12) to the eighth terminal (8) of the fourth transistor (T4). The negative charge pump (LPMB) for the rapid removal of stored charge carriers is also connected via its eleventh terminal (11) to a reference potential; in this diagram, the negative total supply voltage (GND) is shown as the reference potential for the negative charge pump (LPMB) for the rapid removal of stored charge carriers. The positive charge pump (LPPA) for generating a short turn-on edge is connected via its fourteenth terminal (14) to the fifth terminal (5) of the third transistor (T3). The positive charge pump (LPPA) for generating a short turn-on edge is also connected via its thirteenth terminal (13) to a reference potential; in this diagram, the total positive supply voltage (VCC) is shown as the reference potential for the positive charge pump (LPPA) for generating a short turn-on edge. The negative charge pump (LPMA) for generating a short turn-on edge is connected via its fifteenth terminal (15) to the fourth terminal (4) of the second transistor (T2). The negative charge pump (LPMA) for generating a short turn-on edge is also connected via its sixteenth terminal (16) to a reference potential; in this diagram, the negative total supply voltage (GND) is shown as the reference potential for the negative charge pump (LPMA) for generating a short turn-on edge. The depletion region of the LED (LED1) is cleared of remaining charge carriers more quickly when the LED (LED1) is switched off, because the potential of the tenth terminal (10) of the positive charge pump (LPPB) for the rapid removal of the stored charge carriers is higher than the potential of the twelfth terminal (12) of the negative charge pump (LPMB) for the rapid removal of the stored charge carriers, and because the voltage potential of the tenth terminal (10) of the positive charge pump (LPPB) for the rapid removal of the stored charge carriers is higher than that of the positive total supply voltage (VCC), and the voltage potential of the twelfth terminal (12) of the negative charge pump (LPMB) for the rapid removal of the stored charge carriers is lower than that of the negative supply voltage (GND). The junction of the LED (LED1) is flooded with charge carriers more quickly when the LED (LED1) is switched on, because the potential of the fourteenth terminal (14) of the positive charge pump (LPPA) for generating a short turn-on edge is higher than the potential of the fifteenth terminal (15) of the negative charge pump (LPMA) for generating a short turn-on edge, and because the voltage potential of the fourteenth terminal (14) of the positive charge pump (LPPA) for generating a short turn-on edge is higher than that of the positive supply voltage (VCC), and the voltage potential of the fifteenth terminal (15) of the negative charge pump (LPMA) for generating a short turn-on edge is lower than that of the negative total supply voltage (GND). All other sub-devices and processes proceed analogously to Fig. 1. Figure 4 Fig. 4 schematically shows a device corresponding to Fig. 1, but now with a pair of a positive and a negative charge pump to generate a short switching edge. The positive charge pump (LPPA) for generating a short turn-on edge is connected via its fourteenth terminal (14) to the fifth terminal (5) of the third transistor (T3). The positive charge pump (LPPA) for generating a short turn-on edge is also connected via its thirteenth terminal (13) to a reference potential; in this diagram, the total positive supply voltage (VCC) is shown as the reference potential for the positive charge pump (LPPA) for generating a short turn-on edge. The negative charge pump (LPMA) for generating a short turn-on edge is connected via its fifteenth terminal (15) to the fourth terminal (4) of the second transistor (T2). The negative charge pump (LPMA) for generating a short turn-on edge is also connected via its sixteenth terminal (16) to a reference potential; in this diagram, the negative total supply voltage (GND) is shown as the reference potential for the negative charge pump (LPMA) for generating a short turn-on edge. The junction of the LED (LED1) is flooded with charge carriers more quickly when the LED (LED1) is switched on, because the potential of the fourteenth terminal (14) of the positive charge pump (LPPA) for generating a short turn-on edge is above the potential of the fifteenth terminal (15) of the negative charge pump (LPMA) for generating a short turn-on edge, and because the voltage potential of the fourteenth terminal (14) of the positive charge pump (LPPA) for generating a short turn-on edge is higher than that of the positive total supply voltage (VCC), and the voltage potential of the fifteenth terminal (15) of the negative charge pump (LPMA) for generating a short turn-on edge is lower than that of the negative total supply voltage (GND). All other sub-devices and processes proceed analogously to Fig. 1. Figure 5 Fig. 5 schematically shows a device corresponding to Fig. 1, but now with a positive charge pump to generate a short switching edge. The positive charge pump (LPPA) for generating a short turn-on edge is connected via its fourteenth terminal (14) to the fifth terminal (5) of the third transistor (T3). The positive charge pump (LPPA) for generating a short turn-on edge is also connected via its thirteenth terminal (13) to a reference potential; in this diagram, the total positive supply voltage (VCC) is shown as the reference potential for the positive charge pump (LPPA) for generating a short turn-on edge. The junction of the LED (LED1) is flooded with charge carriers more quickly when the LED (LED1) is switched on, because the potential of the fourteenth terminal (14) of the positive charge pump (LPPA) for generating a short switch-on edge is above the potential of the negative supply voltage (GND) and because the voltage potential of the fourteenth terminal (14) of the positive charge pump (LPPA) for generating a short switch-on edge is higher than that of the positive total supply voltage (VCC). All other sub-devices and processes proceed analogously to Fig. 1. Figure 6 Fig. 6 schematically shows a device corresponding to Fig. 1, but now with a negative charge pump to generate a short switching edge. The negative charge pump (LPMA) for generating a short turn-on edge is connected via its fifteenth terminal (15) to the fourth terminal (4) of the second transistor (T2). The negative charge pump (LPMA) for generating a short turn-on edge is also connected via its sixteenth terminal (16) to a reference potential; in this diagram, the negative supply voltage (GND) is shown as the reference potential for the negative charge pump (LPMA) for generating a short turn-on edge. The junction of the LED (LED1) is flooded with charge carriers more quickly when the LED (LED1) is switched on, because the potential of the positive total supply voltage (VCC) is above the potential of the fifteenth terminal (15) of the negative charge pump (LPMA) to generate a short turn-on edge, and because the voltage potential of the fifteenth terminal (15) of the negative charge pump (LPMA) to generate a short turn-on edge is lower than that of the negative total supply voltage (GND). All other sub-devices and processes proceed analogously to Fig. 1. Figure 7 Fig. 7 schematically shows a device corresponding to Fig. 1, but now with a negative charge pump for extracting the stored charge carriers. The negative charge pump (LPMB) for the rapid removal of stored charge carriers is connected via its twelfth terminal (12) to the eighth terminal (8) of the fourth transistor (T4). The negative charge pump (LPMB) for the rapid removal of stored charge carriers is also connected via its eleventh terminal (11) to a reference potential; in this diagram, the negative supply voltage (GND) is shown as the reference potential for the negative charge pump (LPMB) for the rapid removal of stored charge carriers. The depletion region of the LED (LED1) is cleared of remaining charge carriers more quickly when the LED is switched off, because the potential of the positive total supply voltage (VCC) is above the potential of the twelfth terminal (12) of the negative charge pump (LPMB) for the rapid removal of the stored charge carriers, and the voltage potential of the twelfth terminal (12) of the negative charge pump (LPMB) for the rapid removal of the stored charge carriers is lower than that of the negative total supply voltage (GND). All other sub-devices and processes proceed analogously to Fig. 1. Figure 8 Fig. 8 schematically shows a device corresponding to Fig. 1, but now with a positive charge pump for extracting the stored charge carriers. The positive charge pump (LPPB) for the rapid removal of stored charge carriers is connected via its tenth terminal (10) to the first terminal (1) of the first transistor (T1). The positive charge pump (LPPB) for the rapid removal of stored charge carriers is also connected via its ninth terminal (9) to a reference potential; in this diagram, the total positive supply voltage (VCC) is shown as the reference potential for the positive charge pump (LPPB) for the rapid removal of stored charge carriers. The depletion region of the LED (LED1) is cleared more quickly of remaining charge carriers when the LED (LED1) is switched off, because the potential of the tenth terminal (10) of the positive charge pump (LPPB) for the rapid removal of the stored charge carriers is above the negative supply voltage (GND) and because the voltage potential of the tenth terminal (10) of the positive charge pump (LPPB) for the rapid removal of the stored charge carriers is higher than that of the positive total supply voltage (VCC). All other sub-devices and processes proceed analogously to Fig. 1. Figure 9 Fig. 9 schematically shows how a transition from one operating state to the next is possible. The figure shows that preferably only a change from the "PAus" state of the H-bridge (H) (=LED is electrically biased in reverse bias) to the "PZ" state (=no defined voltage is applied to the LED) of the H-bridge (H) or a change from the "PAn" state (=LED is electrically biased in forward bias) of the H-bridge (H) to the "PZ" state (=no defined voltage is applied to the LED) of the H-bridge (H) and vice versa is possible. The "PZ" state describes the initial overall state of the device, in which all control connections (G1, G2, G3, G4) are in a second logic state. This means that all transistors (T1, T2, T3, T4) are in their second operating state (off). The LED (LED1) does not emit light. The "PAn" state describes the second overall state of the device, in which the second control terminal (G2) and the third control terminal (G3) are in a first logic state, and thus the second transistor (T2) and the third transistor (T3) are in the first operating state (conducting). The first control terminal (G1) and the fourth control terminal (G4) are in a second logic state, and thus the first transistor (T1) and the fourth transistor (T4) are in the second operating state (off). The LED (LED1) emits light and is electrically biased in the forward direction. The "PAus" state describes the third overall state of the device, in which the second control terminal (G2) and the third control terminal (G3) are in a second logic state, and thus the second transistor (T2) and the third transistor (T3) are in the second operating state (off). The first control terminal (G1) and the fourth control terminal (G4) are in a first logic state, and thus the first transistor (T1) and the fourth transistor (T4) are in a first operating state (conducting). The LED (LED1) emits no light and is reverse-biased. Figure 9 thus shows, as a state diagram, the minimum permissible overall states "PAn", "PZ", and "PAus" of the H-bridge (H). To avoid a short circuit with an uncontrolled cross current in the branches (T1, T2 / T3, T4) of the H-bridge (H), a transition from the first overall state of the H-bridge (H), the "PAus" state, to the third overall state of the H-bridge (H), the "PZ" state, or vice versa, should first be possible, and / or a transition from the second overall state of the H-bridge (H), the "PAn" state, to the third overall state of the H-bridge (H), the "PZ" state, or vice versa, should first be possible. This reliably prevents the feared cross-current from occurring via the first transistor (T1) of the H-bridge (H) and the second transistor (T2) of the H-bridge (H), which short-circuits the negative charge pump (LPMA) for generating a fast switch-on edge with the positive charge pump (LPPB) for quickly extracting the stored charge carriers and thus consumes their energy reserves. This also reliably prevents the feared cross-current from occurring via the third transistor (T3) of the H-bridge (H) and the fourth transistor (T4) of the H-bridge (H), which short-circuits the negative charge pump (LPMB) with the positive charge pump (LPPA) to generate a fast switch-on edge and thus consumes their energy reserves. However, this idea will be put into perspective in the following. For the purposes of this disclosure, the "PAn" state is assumed for a very short on-time (τpp). To enable rapid on-time, an increased forward voltage (UDR) is applied to the first LED (LED1) in the forward direction. In the "PAus" state, a reverse voltage (URM) is then applied to the first LED (LED1) for another very short clearing time (τpn). The "PAus" state is thus only assumed for this short clearing time (τpn) and then exited. This clearing time (τpn) is preferably dimensioned such that a residual charge of the stored charge remains in the first LED (LED1) after the end of the clearing time (τpn), protecting it from damage by avalanche effects. Figure 10 Fig. 10 shows a simulation comparing three driver circuits (listed from longest to shortest pulse): current driver (20 mA) (reference c), voltage driver (3.3 V) (reference b), and H-bridge (40 V) (reference a). As can be clearly seen, the proposed method is significantly better suited for generating short pulses than other prior art methods. Figure 11 Figure 1 shows the current waveform of the proposed pulsation method and the voltage waveform across the first LED (LED1). For a very short on-time (τpp), a forward voltage (UDR) is applied to the first LED (LED1) in the forward direction. This causes the electric current through the first LED (LED1) to rise very rapidly and steeply. Its depletion region is flooded with charge carriers, preferably without yet reaching a quasi-static equilibrium. Instead, after this on-time (τpp), the polarity of the voltage across the first LED (LED1) is preferably reversed. For a clearing time (τpn), a reverse voltage (URM) is then applied to the first LED (LED1). This clearing time (τpn) is dimensioned such that a residual charge remains in the first LED (LED1).This is the case when the clearing time (τpn) is shorter than the storage time (τSP1) of the charge carriers in the first LED (LED1) when operating it with a forward voltage (UDR) that is typically higher than the supply voltage in pulsed forward operation of the first LED (LED1) and simultaneously using a reverse clearing voltage (URM) that is higher in magnitude than the supply voltage. The storage time (τSP0) of the charge carriers in the first LED (LED1) when operating with a normal, i.e., unincreased, supply voltage (UDR) and using the supply voltage as the reverse clearing voltage (URM) of the first LED (LED1) is also shown. (See also Fig. 10, case b). Figure 12 Figure 12 corresponds to Figure 3 with the addition of an H-bridge control instrument (HCV) for measuring the voltage drop across the load in the first H-bridge (H), typically the lamp voltage (VLED1) across the first LED (LED1). This allows for monitoring the functionality of the control by the first H-bridge (H) and the first LED (LED1) of the H-bridge (H) during operation and, if necessary, for optimizing individual control parameters of the bridge, as explained below. Measuring the lamp voltage (VLED1) across the first LED (LED1) is particularly important because automotive headlights are safety-relevant components of these vehicles. The first LED (LED1) can also be a circuit of several LEDs, specifically an LED string.If one of these LEDs fails, its failure should be measurable and signaled. For this purpose, an H-bridge control instrument (HCV) compares the voltage drop (VLED1) across the first LED (LED1), which we can assume here is part of a chain of several LEDs, with a reference value that corresponds to the current state of the H-bridge (H). If the voltage drop (VLED1) is above a first threshold and below a second threshold that differs from and is preferably higher than the first, it can be concluded that the arrangement of the multiple LEDs is within the permissible tolerance range defined by these thresholds and is therefore functioning correctly. In the other two cases, the H-bridge control instrument (HCV) detects a fault and signals it.For this purpose, the H-bridge control instrument (HCV) signals this measured value of the lamp voltage (VLED1) to a computer system (µC), which may be part of the H-bridge (H) but may also be located in a higher-level context, as described in this disclosure. This signaling of the lamp voltage (VLED1) to a computer system (µC) can also take the form of signaling the temporal profile of the lamp voltage (VLED1). It is therefore proposed that the temporal profile of the lamp voltage (VLED1) during the emission of the light pulse be captured, at least with a sample value.Thus, the computer system (µC) can then, depending on the determined temporal profile of the lamp voltage (VLED1) or a specific value of the lamp voltage (VLED1) at a given time, control the parameters of the first LED (LED1), in particular by adjusting the charge pump voltage of the charge pumps (LPPB, LPPA, LPMB, LPMA), e.g., in the form of the bias voltage of the energy reserves (C_LPPB, C_LPPA, C_LPMB, C_LPMA) of the charge pumps (LPPB, LPPA, LPMB, LPMA) or the voltage converters (SVPB, SVPA, SVMB, SVMA), and by varying the dwell times in the states "PAN", "PAUS", and "ZV". This is explained in more detail below. If the first LED (LED1) is also to be used as a lighting element, the computer system (µC) can also control the supply voltage of the first LED (LED1) and the duty cycle of the PWM with which the control unit (ST) controls the first light-emitting diode (LED1) via the switching elements (T1, T2, T3, T4) of the H-bridge (H).If the first LED (LED1) is part of a multi-LED array, measuring the voltage of individual LEDs within this array can also be useful, allowing for the analysis and monitoring of faults in individual LEDs. Therefore, the diagram in Fig. 12 is merely an example. Figure 13 Fig. 13 corresponds to Fig. 12 with the difference that a first H-bridge control instrument (HCI1) is provided for measuring the current through the first switching element of the H-bridge, i.e., typically through the first transistor (T1), here by detecting the voltage drop across the first transistor (T1); a second H-bridge control instrument (HCI2) is provided for measuring the current through the second switching element of the H-bridge, i.e., typically through the second transistor (T2), here by detecting the voltage drop across the second transistor (T2); a third H-bridge control instrument (HCI3) is provided for measuring the current through the third switching element of the H-bridge, i.e., typically through the third transistor (T3), here by detecting the voltage drop across the third transistor (T3); and a fourth H-bridge control instrument (HCI4) is provided for measuring the current through the fourth switching element of the H-bridge.This is typically achieved by the fourth transistor (T4), specifically by measuring the voltage drop across it. This allows for monitoring the functionality of the control circuitry by the first H-bridge (H) and the first LED (LED1) of the H-bridge (H) during operation, particularly by inferring the current flow. If one of the switching elements (T1, T2, T3, T4) of the H-bridge (H) fails, the voltage drop across that element will no longer correspond to its expected value. The H-bridge, especially in conjunction with an H-bridge control instrument (HCV), is able to control the energy output to the first LED (LED1) and adjust the control signal before critical thresholds are exceeded. In particular, both the current and voltage responses over time can be precisely regulated and optimized. Therefore, it is highly advantageous to...This applies if the output voltage of both the positive charge pumps (LPPB, LPPA) and the negative charge pumps (LPMA, LPMB), or the negative voltage converters (SVMA, SVMB), is adjustable. This adjustment is preferably provided by the controller (ST) or the computer system (µC). Furthermore, it is then advantageous to operate the transistors (T1, T2, T3, T4) not only as switches, but also, if necessary, as current source transistors, and to regulate the current through the first LED (LED1) via these transistors. This makes it possible to define a power transfer profile over time for the first LED (LED1), specifying when and how much energy is supplied to or drawn from the first LED (LED1). During the development of the proposal, it was recognized that it can be quite useful to allow a certain cross-flow in the half-bridges (HB1, HB2) of the H-bridge (H) when switching from an additional cross-flow state “PQZ” to the “PAus” state,because this not only clears the charge carriers more quickly from the first LED (LED1), but also from the switching-off transistors (T2, T3). It was recognized that for the transition from the "PAus" state to the "PAn" state, it is advantageous and preferable to actually pass through the "PZ" state, whereby at the end of the time spent in the "PZ" state, all transistors of both half-bridges (HB1: T1, T2; HB2: T3, T4) are completely off. This distinguishes the "PZ" state from the "QPZ" state described later. Since the charge carriers in the transistors previously switched on in the "PAus" state (in this example, the first transistor T1 and the fourth transistor T4) are then only dissipated very slowly, this state must be maintained for a minimum duration (TPZmin). Only then can the transition from the "PZ" state to the "PAn" state occur. (See also Fig. 9) For the reverse case of the transition from the "PAn" state to the "PAus" state, the situation is different. Here, the first LED (LED1) and the switching-off transistors (in this example, the second transistor T2 and the third transistor T3) should be cleared of charge carriers as quickly as possible. Since the switching-off transistors (in this example, the second transistor T2 and the third transistor T3) require some time to switch off, it is advantageous to allow a cross-current through the switching-on transistors (in this example, the first transistor T1 and the fourth transistor T4) at the beginning of the "PAn" state. This achieves two effects: First, the switching-off transistors (in this example, the second transistor T2 and the third transistor T3) are discharged more quickly by the switching-on transistors (in this example, the first transistor T1 and the fourth transistor T4).The switching-on transistors therefore also absorb a large part of the respective currents that the switching-off transistors (in the example the second transistor T2 and the third transistor T3) would otherwise still supply to the first LED (LED1). Secondly, this leads to a faster polarity reversal and thus discharge of the first LED (LED1). It is therefore advantageous to maximize the permissible cross-currents in the respective half-bridges (HB1, HB2) during the turn-off of the switching-off transistors (in this example, the second transistor T2 and the third transistor T3) during the transition from the "PAn" state to the "PAus" state, up to the thermal limit. This means that the transition from the "PAn" state to the "PAus" state preferably occurs via a "PQZ" state in which a cross-current is briefly permitted that is larger than the cross-current in the "PZ" state. To achieve the aforementioned cross-current maximization in the "PQZ" state, it is particularly advantageous to be able to measure the essential parameters of the energy loss in the transistors (T1, T2, T3, T4).Since the behavior of the transistors (T1, T2, T3, T4), especially their on-resistance, is generally known, it is useful to calculate the respective energy output based on the voltage drops across the transistors (T1, T2, T3, T4). The axial current of the H-bridge through the first LED (LED1) can usually be estimated from the voltage drop across the first LED (LED1). In this context, it can be advantageous to measure the current precisely using two shunt resistors (Rs1, Rs2), for example, in the ground lines of the H-bridge (H) (see Fig. 23), rather than simply estimating it from the voltage drop across the transistors (T1, T2, T3, T4). Since the function of the transistors (T1, T2, T3, T4) is different, the first transistor (T1) of the H-bridge (H) is typically not the same as the third transistor (T3) of the H-bridge (H), and the second transistor (T2) of the H-bridge (H) is typically not the same as the fourth transistor (T4) of the H-bridge (H).The precise dimensions will be determined by a person skilled in the art through calculation and simulation, taking into account the first LED (LED1) used and the layout of the typically employed printed circuit board. The control of the cross-currents in the two states "PZ" and "PQZ" is preferably achieved by controlling the voltage of the charge pumps (LPPA, LPPB, LPMA, LPMB) or the voltage converters (SVPA, SVPB, SVMA, SVMB) and by controlling the switch-on and switch-off times of the transistors (T1, T2, T3, T4). The actual values ​​used for such control can be the voltage across the first LED (LED1), the voltage drops across the transistors (T1, T2, T3, T4), and, if necessary, additional measured values ​​for the current through the respective half-bridges (HB1: T1, T2; HB2: T3, T4). It is known from the prior art (e.g., US 4 571506 A, column 2, lines 59 to 65) that higher reverse voltages applied to an LED lead to a reduction in the storage time (τSP0). It is also known from the prior art that the maximum permissible peak reverse voltage is limited by the breakdown characteristics of the LED. According to the invention, it has now been discovered that the n- and p-charge carriers still present in the depletion region prevent the formation of high electric field strengths within the PN junction of the first LED (LED1) at the beginning of the discharge process, as long as such mobile space charge clouds are still located in the depletion region. This results in a current limited by the dynamic space charge.Furthermore, it was observed that the luminous efficacy had already decreased before all charges were removed from the depletion region, as the centers of positive charge of the holes and negative charge of the electrons converge. Therefore, it is generally sufficient to remove a significant portion of the space charge, but not all of it. It is thus advantageous to apply a large forward voltage (UDR) to the first LED (LED1) for a very short on-time (τpp), so that it is quickly flooded with charge carriers, and then to apply a very large reverse voltage for a very short off-time (τpn), which is shorter than the resulting storage time (τsp1) that would result from this reverse voltage.The clearing time (τpn) should preferably be less than 95% of the storage time (τsp1), preferably less than 95% of the storage time (τsp1), preferably less than 90% of the storage time (τsp1), preferably less than 85% of the storage time (τsp1), preferably less than 80% of the storage time (τsp1), preferably less than 75% of the storage time (τsp1). It is recommended to accurately assess the impact on the junction and the lifetime of the LEDs and to adjust the clearing time (τpn) accordingly. The residual charge remaining in the first LED (LED1) protects it from an avalanche breakdown, as the charge cloud of the residual charge prevents the development of a high electric field strength within the LED. On the cathode side, the early switch-off of the turn-off voltage prevents cathode fall by electrons, and on the anode side, it prevents anode fall by holes, since these charge carriers are still in the drift path at this point of switch-off. Unlike US 4 571 506 A, which only specifies a small reverse voltage of 0.2 Vdc (column 2, lines 27 to 32 of US 4 571 506 A) across the LED to be switched off, here a much larger reverse voltage, preferably with a magnitude close to the forward voltage, is applied to the first LED (LED1). The technical teaching of US 4 571 506 A failed to recognize that sufficient residual charge after the accelerated switch-off of the LED is critical for the lifespan of the LED being energized, as this is the only way to prevent the development of high field strengths. Another important point is the prevention of thermal breakdown of the LED. It was recognized that the heat input into the LED must be limited. Therefore, the pulse repetition frequency for generating such high-power pulses must be chosen to be lower the higher the applied voltage.Since the pulse power increases quadratically with the voltage, the pulse interval must be increased and / or the pulse duration decreased to limit the average input power. Once the residual charge is dissipated, a strong electric field develops inside the LED, which can lead to the LED's destruction through avalanche effects. This operating condition must therefore be strictly avoided. The turn-on time (τpp) and the turn-off time (τpn) can be controlled, for example, by suitable timers such as delay circuits. If the storage times (τSP0, τSP1) of the first LED (LED1) are known as a function of the applied voltages, these times can be set constructively. Preferably, a temperature dependency is taken into account. For example, programmable delay circuits can be used for the operating-state-dependent setting of these times together with a suitable start signal, which is then adjusted by these delay circuits. Furthermore, it can be useful to equip the transistors (T1, T2 / T3, T4) with one or more thermocouples that monitor the transistors during operation. Their parameters can also be used for control. It is therefore particularly advantageous to thermally couple at least one of the transistors (T1, T2 / T3, T4) to a temperature sensor, especially a PN diode or a bipolar transistor. If the transistors (T1, T2 / T3, T4) of the H-bridge (H) are MOS transistors, it is especially useful if the at least one temperature sensor is located at the center of a symmetry point of such a transistor. For example, it is advantageous to implement such a MOS transistor in a square shape and to place a small PN diode or a bipolar transistor at the geometric center of the transistor. The diode voltage, or the diode voltage of the base-emitter diode, is temperature-dependent and can be measured. Therefore, it can be used as a current source for regulating the current through the half-bridges (HB1, HB2) of the H-bridge. To regulate the current, at least one transistor (e.g. T2) is used as a current source transistor. Figure 14 Fig. 14, like Fig. 9, schematically illustrates how a transition from one operating state to the next is possible. However, it is now assumed that during the transition from the "PAn" state, in which the first transistor (T1) and the fourth transistor (T4) are off and the second transistor (T3) and the third transistor (T4) are on, to the "PAus" state, in which the first transistor (T1) and the fourth transistor (T4) are on and the second transistor (T3) and the third transistor (T4) are off, a different cross-current is desired than during the transition from the "PAus" state to the "PAn" state. (See also the description of Fig. 13.) Firstly, only a transition from the "PAus" state of the H-bridge (H) (=LED is reverse-biased), in which the first transistor (T1) and the fourth transistor (T4) are conducting and the second transistor (T3) and the third transistor (T3) are blocking, to the "PZ" state (=no defined voltage is applied to the LED and preferably all transistors are off), in which preferably the first transistor (T1) and the fourth transistor (T4) are conducting and the second transistor (T3) and the third transistor (T3) are blocking, is possible. The reverse transition is no longer desired. Secondly, the only preferred transition is from the "PZ" state of the H-bridge (H), in which the first transistor (T1) and the fourth transistor (T4) are preferably off, and the second transistor (T3) and the third transistor (T3) are preferably off, to the "PAn" state (=LED is forward-biased), in which the first transistor (T1) and the fourth transistor (T4) are off and the second transistor (T3) and the third transistor (T3) are on. The reverse transition is no longer desired. Thirdly, only a transition from the "PAn" state of the H-bridge (H), in which the first transistor (T1) and the fourth transistor (T4) are off and the second transistor (T3) and the third transistor (T3) are on, to the additional "PQZ" state (= A certain cross current in the H-bridge (H) is allowed.), in which the first transistor (T1) and the fourth transistor (T4) are off and the second transistor (T3) and the third transistor (T3) are off, is preferably possible. The reverse transition is no longer desired. Fourthly, the only preferred transition is from the additional "PQZ" state of the H-bridge (H), in which the first transistor (T1) and the fourth transistor (T4) are preferably off, and the second transistor (T3) and the third transistor (T3) are off, to the "PAus" state of the H-bridge (H), in which the first transistor (T1) and the fourth transistor (T4) are on, and the second transistor (T3) and the third transistor (T3) are off. The reverse transition is no longer desired. The "PZ" state, as before, describes the first overall state of the device, in which the first transistor (T1) and the fourth transistor (T4) are off, and the second transistor (T3) and the third transistor (T4) are off. In the first overall state, the "PZ" state, all control terminals (G1, G2, G3, G4) are preferably in a second logic state. This means that all transistors (T1, T2, T3, T4) are preferably in their second operating state (off). The LED (LED1) does not emit light. The "PAn" state describes the second overall state of the device, in which the second control terminal (G2) and the third control terminal (G3) are in a first logic state, and thus the second transistor (T2) and the third transistor (T3) are in the first operating state (conducting). The first control terminal (G1) and the fourth control terminal (G4) are in a second logic state, and thus the first transistor (T1) and the fourth transistor (T4) are in the second operating state (off). The LED (LED1) emits light and is electrically biased in the forward direction. The "PAus" state describes the third overall state of the device, in which the second control terminal (G2) and the third control terminal (G3) are in a second logic state, and thus the second transistor (T2) and the third transistor (T3) are in the second operating state (off). The first control terminal (G1) and the fourth control terminal (G4) are in a first logic state, and thus the first transistor (T1) and the fourth transistor (T4) are in a first operating state (conducting). The LED (LED1) emits no light and is reverse-biased. The “PQZ” state describes the fourth overall state of the device, in which the control of the control terminals (G1, G2, G3, G4) is carried out in such a way that the second transistor (T2) and the third transistor (T3) transition from the first operating state (conducting) to the second operating state (off) as quickly as possible, and the first control terminal (G1) and the fourth control terminal (G4) are in a first logical state, and thus the first transistor (T1) and the fourth transistor (T4) are in a first operating state (conducting).A cross-current typically occurs because, due to the typically short dwell time in the "PQZ" state, the second transistor (T2) and the fourth transistor (T4) are usually not completely switched off when exiting the "PQZ" state and entering the "PAus" state. Therefore, the first transistor (T1) is already supplying electrical current, which is then directly absorbed by the second transistor (T2). It is therefore of particular importance that, firstly, the time (Δt) during which the H-bridge (H) is in this "PQZ" state is precisely controlled, preferably regulated, and secondly, that the cross-current occurring in the half-bridges (HB1: T1, T2; HB2: T3, T4) of the H-bridge (H) in the subsequent "PAus" state is also preferably precisely controlled, and preferably regulated via a current source circuit over the time course of the cross-current.If cross-currents are to be actively utilized, it is conceivable to assume one of the cross-current states from Table 1 as an additional temporary state for a defined period of time within the "PQZ" state. In such a provoked cross-current state, this current should preferably be limited by current source transistors (T2, T4) and, even more preferably, controlled or regulated. The LED (LED1) switches off in this "PQZ" state. The H-bridge (H) changes the voltage applied to the first LED (LED1) from forward to reverse bias in this "PQZ" state.The second overall state, the "PAn" state, is maintained during light pulse operation for no longer than a switch-on time (τpp), which is preferably shorter than the charge carrier lifetime (τ), since, according to the technical teaching proposed here, the control is achieved with an increased operating voltage in the forward direction of the LEDs during this light pulse operation. Similarly, the third overall state, the "PAus" state, is also maintained for no longer than a clearing time (τpn), where the clearing time (τpn) is shorter than the charge carrier lifetime (τ), since, according to the technical teaching proposed here, the control is achieved with an increased operating voltage in the reverse direction of the LEDs during this light pulse operation. It is of particular importance that the space charge region of the LEDs must not be discharged. The switch-on time (τpp) must be shorter than the charge carrier lifetime (τ). Figure 14 thus shows, as a state diagram, the at least permissible total states "PQZ", "PAn", "PZ", and "PAus" of the H-bridge (H). Further states are conceivable (see Table 1). The states with cross-current are typically blocked, as listed in the table. To clear charge carriers, etc., a preferably very short-term assumption of these states marked "blocked" is conceivable, for example, if transistors (e.g., T2, T4) of the H-bridge are operated as current source transistors or if the power dissipated is otherwise sensibly limited. Table 1: States of the proposed H-bridge (H) in its simplest implementation. 1 off off off arbitrarily illuminated not "PZ" state 2anausausausausanylights nottnv. 3 off on off off anytime it lights up not tnv. 4ananausaus crossflow in the first half-bridge (HB1) blocked 5ausausanausleuchtet nichttnv. 6 on off on off Clearing time (τpn) does not light up, charges are being cleared LED1 off “PA off” state 7 off on off Switch-on time (τpp) illuminates “PAn” state 8anananaus crossflow in the first half-bridge (HB1) blocked 9ausausausanbelarigleuchtet nichttnv. 10 on off off on any light does not light up, LED1 is short-circuited via positive supply voltage “k” state (1st variant) 11 off on off on any light does not light up, LED1 is short-circuited via negative supply voltage “k” state (2nd variant) 12ananausan crossstream in the first half-bridge (HB1) blocked 13ausausanan Crossstream in the second half-bridge (HB2) blocked 14anausananQuerstrom in the second half-bridge (HB2)blocked 15ausananan crossstream in the second half-bridge (HB2) blocked 16anananan Crossstream in the first half-bridge (HB1) and in the second half-bridge (HB2) blocked tnv. = typically not used, but permissible. Only by precisely controlling the cross-current in the "PQZ" state can it be avoided that an uncontrolled cross-current occurs through the first transistor (T1) of the H-bridge (H) and the second transistor (T2) of the H-bridge (H), which short-circuits the negative charge pump (LPMA) for generating a fast turn-on edge with the positive charge pump (LPPB) for quickly extracting the stored charge carriers and thus consumes their energy reserve uncontrollably or damages the H-bridge (H) or, in the case of a voltage converter (SVPB), damages the voltage converter (SVPB) instead of the charge pump (LPPB). This precise control of the cross-current in the "PQZ" state also prevents uncontrolled cross-current flowing through the third transistor (T3) and the fourth transistor (T4) of the H-bridge (H). Such a short circuit would cause the negative charge pump (LPMB), used for rapidly discharging stored charge carriers, to short-circuit the positive charge pump (LPPA), used to generate a fast turn-on edge. This would result in uncontrolled consumption of the H-bridge's energy reserve, damage to the H-bridge (H), or, in the case of a voltage converter (SVMB), damage to the voltage converter (SVMB) instead of the charge pump (LPMB). It is obvious that when using a “PQZ” state, the energy reserves (C_LPPA, C_LPPB, C_LPMA, C_LPMB) of the charge pumps (LPPA, LPPB, LPMA, LPMB) must be chosen to have a larger capacity in order to compensate for the energy losses caused by the cross-current. In the case of using voltage converters (SVPA, SVPB, SVMA, SVMB) instead of charge pumps (LPPA, LPPB, LPMA, LPMB), their internal resistances must be chosen appropriately. The second overall state, the "PAn" state, is maintained during pulsed light operation for no longer than a switch-on time (τpp), which is preferably shorter than the charge carrier lifetime (τ), since, according to the proposed technical teaching, the control signal is applied with an increased operating voltage in the forward direction of the LEDs during this pulsed light operation. Similarly, the third overall state, the "PAus" state, is also maintained for no longer than a clearing time (τpn), where the clearing time (τpn) is shorter than the charge carrier lifetime (τ), since, according to the proposed technical teaching, the control signal is applied with an increased operating voltage in the reverse direction of the LEDs during this pulsed light operation. It is particularly important that the space charge region of the LEDs is not discharged. The switch-on time (τpp) must be shorter than the charge carrier lifetime (τ). Figure 15 Fig. 15 shows an exemplary, proposed headlight system (SW) in a schematically simplified and functionally symbolic way, wherein the light source, the first LED (LED1), can be used both in pulsed operation in a pulsed operating state (GPB) and as a light source for quasi-continuous illumination in a quasi-continuous operating state (QDB). The H-bridge (H) is connected to the anode (A) of the first LED (LED1) via the second terminal (2) of the first transistor (T1) of the first half-bridge (HB1) of the H-bridge (H). The H-bridge (H) is connected to the anode (A) of the first LED (LED1) via the third terminal (3) of the second transistor (T2) of the first half-bridge (HB1) of the H-bridge (H). The H-bridge (H) is connected to the cathode (K) of the first LED (LED1) via the sixth terminal (6) of the third transistor (T3) of the second half-bridge (HB2) of the H-bridge (H). The H-bridge (H) is connected to the cathode (K) of the first LED (LED1) via the seventh terminal (7) of the fourth transistor (T4) of the second half-bridge (HB2) of the H-bridge (H). In this example, the H-bridge (H) is supplied with a positive total supply voltage (VCC) and is connected to the negative total supply voltage (GND). For the sake of simplicity, the supply voltage lines of the other bridges are not shown, as is generally the case in this disclosure. A control unit (ST) generates the control signal for the first control terminal (G1) of the first transistor (T1) of the H-bridge (H). The control unit (ST) generates the control signal for the second control terminal (G2) of the second transistor (T2) of the H-bridge (H). The control unit (ST) generates the control signal for the third control terminal (G3) of the third transistor (T3) of the H-bridge (H). The control unit (ST) generates the control signal for the fourth control terminal (G4) of the fourth transistor (T4) of the H-bridge (H). If the charge pumps (LPPA, LPPB, LPMA, LPMB) or voltage converters (SVPA, SVPB, SVMA, SVMB) of the H-bridge (H) (not shown) require a clock signal (clk3) for their operation, this is preferably provided by a common time base (TB) as the base time signal (clk3) of the H-bridge (H). The time base (TB) generates the base time signals (clk1, clk2, clk3) of the device. These are preferably the base time signal (clk1) (typically = base clock) of a computer system (µC) that preferably controls the entire device, the base time signal (clk2) (typically = base clock) of the control unit (ST) for directly controlling the H-bridge (H), and the aforementioned base time signal (clk3) (typically = base clock) of the H-bridge (H). These base time signals can be interdependent or identical. The control unit (ST) is preferably a mixed analog / digital circuit. Provided a state diagram according to Fig.9, the control device can also be a purely digital finite-state machine that generates purely digital control signals (G1, G2, G3, G4) for the transistors (T1, T2, T3, T4) of the H-bridge. However, if one of the transistors (e.g., T2, T4) in each half-bridge (HB1: T1, T2; HB2: T3, T4) of the H-bridge (H) is to be used not only as a switching element but also as a current source transistor, the control device (ST) must detect the gate-source voltage of these transistors (e.g., T2, T4) used as current sources in the respective half-bridge (HB1, HB2) of the H-bridge (H) and adjust it in comparison to a voltage reference, e.g., the voltage across a reference current-carrying MOS transistor diode, provided they are in a state in which they are not switched off. The control unit (ST) also typically generates the correct timing behavior when traversing the state diagrams, e.g., in Fig. 9, Fig. 14, and Fig. 22. Furthermore, the control unit preferably sets the voltage of the charge pumps (LPPA, LPPB, LPMA, LPMB), if used, or the voltage converters (SVPA, SVPB, SVMA, SVMB), if used. The control unit (ST) is preferably controlled by the exemplary computer system (µC). This preferably acquires all measurement parameters acquired in the device and, if necessary, adjusts the operating parameters accordingly. The computer system (µC) preferably communicates with the control unit (ST) via an internal data bus (IB). The computer system (µC) transmits essential operating parameters to the control unit (ST), such as the setting for which type of state diagram should be used, how long the control unit (ST) may keep the H-bridge (H) in the "PQZ" state, or which cross-currents should be set, for example, when entering the "PAus" state, e.g., by means of a current source transistor (e.g., T2), etc. If the supply voltage (VCC) originates from a voltage regulator, which may...Since the H-bridge is part of the device, it is advantageous for its operating parameters, particularly the voltage (VCC) relative to the reference potential (here GND), to also be controlled by the computer system (µC). This also applies, if applicable, to voltage converters (SVPA, SVPB, SVMA, SVMB) or charge pumps (LPPA, LPPB, LPMA, LPMB) for supplying the H-bridge (H). The computer system (µC) communicates via a data bus (DB) with hierarchically higher-level computer systems not shown in the figures, e.g., a control unit in a vehicle. The light pulses (LP) generated by the first LED (LED1) are coupled out of the headlight (SW) into the outside space via optics (OP) and, if necessary, by means of mirror optics (RF). Other emission directions are typically suppressed by apertures (BL). Figure 16 Figure 16 shows an exemplary modified H-bridge (H) for use in a device according to Figure 15 and in modification of Figure 3. In contrast to the H-bridge of Figure 3, the H-bridge (H) of Figure 16 and the first LED (LED1) can now be used both for the emission of optimized light pulses (LP) and for optimized light emission for illumination purposes by switching between a power supply based on charge pumps (LPPA, LPPB, LPMA, LPMB) or on voltage converters (SVPA, SVPB, SVMA, SVMB) and a direct power supply from the total supply voltages (VCC, GND) by means of additional transistors (T5, T6, T7, T8, T9, T10, T11, T12). If the first LED (LED1) is to be operated in a first operating mode, in which the first LED (LED1) is used as a light source for lighting purposes (e.g., headlights) in quasi-continuous operation (QDB), and in time-division multiplexing it is to be operated in a second operating mode, in which the first LED (LED1) is used as a measuring light source to generate light pulses (LP) in pulsed operation (GPB), then it is advantageous if the H-bridge (H) can be operated with different operating voltage sources, each assigned to these two operating modes and optimized for them. In the example of Fig. 16, the problem is solved using the example of an H-bridge (H) of Fig. 3 by inserting an analog multiplexer (T9, T5; T8, T12; T10, T6; T7, T11) between the transistors (T1, T2, T3, T4) and their respective charge pump (LPPA, LPPB, LPMA, LPMB) or their respective voltage converter (SVPA, SVPB, SVMA, SVMB), which makes it possible to connect the respective transistor (T1, T2, T3, T4) directly to the respective total supply voltages (VCC, GND) in quasi-continuous operation (QDB) and to connect it to the output (9, 12, 13, 15) of the respective charge pump (LPPA, LPPB, LPMA, LPMB) or the respective voltage converter (SVPA, SVPB, SVMA, SVMB) in pulsed operation (GPB). The switching is performed by the control unit (ST) of the H-bridge (H). In detail, the task of increasing the voltage at the light source, the first LED (LED1), to improve the flooding and removal of charge carriers from the light source, the first LED (LED1), is solved as follows: The first transistor (T1) is not connected with its first terminal (1) to the tenth terminal (10) of the positive charge pump (LPPB) or voltage converter (SVPB) for the rapid removal of the stored charge carriers, but rather to the twenty-sixth terminal (26) of the fifth transistor (T5). This fifth transistor (T5) is then connected with its twenty-sixth terminal (26) to the tenth terminal (10) of the positive charge pump (LPPB) or voltage converter (SVPB) for the rapid removal of the stored charge carriers. The fifth transistor (T5) is thus connected between the tenth terminal (10) of the positive charge pump (LPPB) or voltage converter (SVPB) for the rapid removal of the stored charge carriers.A voltage converter (SVPB) is connected to the first terminal (1) of the first transistor (T1) for the rapid extraction of the stored charge carriers. The fifth transistor (T5) is controlled by the control unit (ST) via the fifth control terminal (G5) of the fifth transistor (T5). Furthermore, the first transistor (T1) is connected via its first terminal (1) to the eighteenth terminal (18) of the ninth transistor (T9). In the example shown in Fig. 16, this ninth transistor (T9) is then connected via its seventeenth terminal (17) to the positive supply voltage (VCC). Thus, the ninth transistor (T9) bypasses the positive charge pump (LPPB) or voltage converter (SVPB) for the rapid removal of the stored charge carriers when it is switched on by the control unit (ST). To prevent short-circuiting the positive charge pump (LPPB) or voltage converter (SVPB) for the rapid removal of the stored charge carriers, the fifth transistor (T5) must be switched off by the control unit (ST) when the ninth transistor (T9) is electrically switched on by the control unit (ST).The ninth transistor (T9), however, must be off when the fifth transistor (T5) is switched on by the control unit (ST). The fifth transistor (T5) and the ninth transistor (T9) thus constitute a first analog multiplexer, which is controlled by the control unit (ST). The ninth transistor (T9) is controlled by the control unit (ST) via the ninth control terminal (G9) of the ninth transistor (T9). The third transistor (T3) is not connected via its fifth terminal (5) to the fourteenth terminal (14) of the positive charge pump (LPPA) or voltage converter (SVPA) for generating a fast turn-on edge, but rather to the thirtieth terminal (30) of the eighth transistor (T8). This eighth transistor (T8) is then connected via its twenty-ninth terminal (29) to the fourteenth terminal (14) of the positive charge pump (LPPA) or voltage converter (SVPA) for generating a fast turn-on edge. Thus, the eighth transistor (T8) is connected between the fourteenth terminal (14) of the positive charge pump (LPPA) or voltage converter (SVPA) for generating a fast turn-on edge and the fifth terminal (5) of the third transistor (T3). The eighth transistor (T8) is controlled by the control unit (ST) via the eighth control terminal (G8) of the eighth transistor (T8). Furthermore, the third transistor (T3) is connected via its fifth terminal (5) to the twenty-second terminal (22) of the twelfth transistor (T12). In the example shown in Fig. 16, this twelfth transistor (T12) is then connected via its twenty-first terminal (21) to the positive total supply voltage (VCC). Thus, the twelfth transistor (T12) bypasses the positive charge pump (LPPA) or voltage converter (SVPA) to generate a fast turn-on edge when it is switched on by the control unit (ST). To prevent short-circuiting the positive charge pump (LPPA) or voltage converter (SVPA) when generating a fast turn-on edge, the eighth transistor (T8) must be switched off by the control unit (ST) when the twelfth transistor (T12) is switched on by the control unit (ST). The twelfth transistor (T12), however, must be off when the eighth transistor (T8) is switched on by the control unit (ST).The eighth transistor (T8) and the twelfth transistor (T12) thus constitute a second analog multiplexer, which is controlled by the control unit (ST). The twelfth transistor (T12) is controlled by the control unit (ST) via the twelfth control pin (G12) of the twelfth transistor (T12). The second transistor (T2) is not connected at its fourth terminal (4) to the fifteenth terminal (15) of the negative charge pump (LPMA) or voltage converter (SVMA) for generating a fast turn-on edge, but rather to the twenty-seventh terminal (27) of the sixth transistor (T6). This sixth transistor (T6) is then connected at its twenty-eighth terminal (28) to the fifteenth terminal (15) of the negative charge pump (LPMA) or voltage converter (SVMA) for generating a fast turn-on edge. Thus, the sixth transistor (T6) is connected between the fifteenth terminal (15) of the negative charge pump (LPMA) or voltage converter (SVMA) for generating a fast turn-on edge and the fourth terminal (4) of the second transistor (T2). The sixth transistor (T6) is controlled by the control unit (ST) via the sixth control terminal (G6) of the sixth transistor (T6). Furthermore, the second transistor (T2) is connected via its fourth terminal (4) to the nineteenth terminal (19) of the tenth transistor (T10). In the example shown in Fig. 16, this tenth transistor (T10) is connected via its twentieth terminal (20) to the negative supply voltage (GND). Thus, the tenth transistor (T10) bypasses the negative charge pump (LPMA) or voltage converter (SVMA) to generate a fast turn-on edge when it is switched on by the control unit (ST). To prevent short-circuiting the negative charge pump (LPMA) or voltage converter (SVMA) when generating a fast turn-on edge, the sixth transistor (T6) must be switched off by the control unit (ST) when the tenth transistor (T10) is switched on by the control unit (ST). The tenth transistor (T10), however, must be off when the sixth transistor (T6) is switched on by the control unit (ST).The sixth transistor (T6) and the tenth transistor (T10) thus constitute a third analog multiplexer, which is controlled by the control unit (ST). The tenth transistor (T10) is controlled by the control unit (ST) via the tenth control pin (G10) of the tenth transistor (T10). The fourth transistor (T4) is not connected via its eighth terminal (8) to the twelfth terminal (12) of the negative charge pump (LPMB) or voltage converter (SVMB) for the rapid removal of stored charge carriers, but rather to the thirty-first terminal (31) of the seventh transistor (T7). This seventh transistor (T7) is then connected via its thirty-second terminal (32) to the twelfth terminal (12) of the negative charge pump (LPMB) or voltage converter (SVMB) for the rapid removal of stored charge carriers. Thus, the seventh transistor (T7) is connected between the twelfth terminal (12) of the negative charge pump (LPMB) or voltage converter (SVMB) for the rapid removal of stored charge carriers and the eighth terminal (8) of the fourth transistor (T4). The seventh transistor (T7) is controlled by the control unit (ST) via the seventh control terminal (G7) of the seventh transistor (T7). Furthermore, the fourth transistor (T4) is connected via its eighth terminal (8) to the twenty-third terminal (23) of the eleventh transistor (T11). In the example shown in Fig. 16, this eleventh transistor (T11) is connected via its twenty-fourth terminal (24) to the negative supply voltage (GND). Thus, the eleventh transistor (T11) bypasses the negative charge pump (LPMB) or voltage converter (SVMB) for the rapid removal of stored charge carriers when it is switched on by the control unit (ST). To prevent short-circuiting the negative charge pump (LPMB) for the rapid removal of stored charge carriers, the seventh transistor (T7) must be switched off by the control unit (ST) when the eleventh transistor (T11) is electrically switched on by the control unit (ST). The eleventh transistor (T11), however, must be off when the seventh transistor (T7) is switched on by the control unit (ST).The seventh transistor (T7) and the eleventh transistor (T11) thus constitute a fourth analog multiplexer, which is controlled by the control unit (ST). The eleventh transistor (T11) is controlled by the control unit (ST) via the eleventh control pin (G11) of the eleventh transistor (T11). Figure 17 Fig. 17 corresponds to Fig. 16 with the difference that the charge pumps (LPPB, LPPA, LPMA, LPMB) and voltage converters (SVPA, SVPB, SVMA, SVMB) are supplied from a fifth supply voltage source (VCC5), and for operation as a light source in a lighting device, the supply is provided directly from a sixth supply voltage source (VCC6) and ground (GND). Preferably, the sixth supply voltage source (VCC6) is the output of a sixth voltage regulator (SR6) for providing the sixth supply voltage (VCC6). The fifth supply voltage source (VCC5) is preferably the output of a fifth voltage regulator (SR5) for providing the fifth supply voltage (VCC5).Preferably, when using the first LED (LED1) for illumination purposes in quasi-continuous operation (QDB), it is supplied from the sixth positive supply voltage (VCC6) and the sixth negative supply voltage (GND6). When used in pulsed operation (GPB), the first LED (LED1) is preferably supplied from the fifth supply voltage source (VCC5) and the fifth negative supply voltage source (GND5). For example, the output voltage of the sixth voltage regulator (SR6) at its outputs (VCC6, GND6) can be equal to the forward voltage of the first LED (LED1). The sixth voltage regulator (SR6) is intended here as an example to provide the sixth positive supply voltage (VCC6) and the sixth negative supply voltage (GND6). The fifth voltage regulator (SR5) is intended here, by way of example, to provide the fifth positive supply voltage (VCC5) and the sixth negative supply voltage (GND5). The output voltage of the fifth voltage regulator (SR5) should preferably be close to the vehicle electrical system voltage (e.g. 12V) of a motor vehicle (VV) at its outputs (VCC5, GND5). Figure 18 Figure 15 shows an exemplary modified H-bridge (H) for use in a device according to Figure 15 and as a modification of Figure 3. In contrast to the H-bridge of Figure 3, the H-bridge (H) of Figure 15 can be used in a modified form. Fig. 18 and the first LED (LED1) can now be used both for the emission of optimized light pulses (LP) in pulsed operation (GPB) and for optimized light emission for lighting purposes in quasi-continuous operation (QDB), by means of a first analog multiplexer (T9, T5) and a second analog multiplexer (T8, T12) to switch between a. the direct power supply from a third positive supply voltage source (VCC3) and a fourth positive supply voltage source (VCC4) for the operation of the first LED (LED1) as a light source of a lighting device in quasi-continuous operation (QDB) on the one hand, and b. the direct power supply from a first positive supply voltage source (VCC1) and a second positive supply voltage source (VCC2) for pulsed operation (GPB) as a pulsed LED (LED1) on the other hand.In this configuration of the proposal, no charge pumps (LPPA, LPPB, LPMA, LPMB) or voltage regulators (SVPA, SVPB, SVMA, SVMB) are preferably provided alongside the first voltage regulator (SR1) and the second voltage regulator (SR2). Preferably, the first supply voltage (VCC1) is the output of a first voltage regulator (SR1). The second supply voltage (VCC2) is again preferably the output of a second voltage regulator (SR2). The third supply voltage (VCC3) is again preferably the output of a third voltage regulator (SR3). The fourth supply voltage (VCC4) is again preferably the output of a fourth voltage regulator (SR4). In the example shown in Fig. 18, the negative total supply voltage (GND) is used as the negative supply voltage. Preferably, when the first LED (LED1) is used for lighting purposes in quasi-continuous operation (QDB), it is supplied from the third and fourth supply voltages (VCC3, VCC4). When used in pulsed operation (GPB), the first LED (LED1) is preferably supplied from the first and second supply voltages (VCC11, VCC2). For example, the output voltage of the first and second voltage regulators (SR1, SR2) at their outputs, the first and second supply voltages (VCC1, VCC2), can be approximately equal to the forward voltage of the first LED (LED1), while the output voltage of the third and fourth voltage regulators (SR3, SR4) at their outputs, the third and fourth supply voltage sources (VCC3, VCC4), is preferably close to the on-board voltage (e.g., 12V) of a motor vehicle.Note that no analog multiplexers are provided in the negative branches of the half-bridge, as an increase in the magnitude of the total negative supply voltage (GND) is not intended here. Preferably, the control unit (ST) supplies a reference voltage at the second control terminal (G2) of the second transistor (G2) when it is to be switched on, so that the second transistor (T2) operates as a transistor current source when switched on. This is particularly advantageous when the first LED (LED1) is operating in quasi-continuous mode (QDB) as a light source for illumination purposes. This controls the amount of energy continuously dissipated in the first LED (LED1). The fourth and third voltage regulators (SR3, SR4), which generate the third and fourth supply voltages (VCC3, VCC4), can then be implemented as switching regulators, while the control losses in the second transistor (T2) are minimized in this quasi-continuous operation, thus minimizing the heating of the second transistor (T2).It was therefore recognized during the development of the proposal that it is advantageous to generate the positive supply voltage (VCC3, VCC4) for the supply of the first LED (LED1) in quasi-continuous operation (QDB) in a switching regulator as a voltage regulator (SR3, SR4) and at the same time to regulate the current in quasi-continuous operation (QDB) by the second transistor (T2) as a current source transistor. In the example shown in Fig. 18, the pulsed current for pulsed operation (GPB) is also regulated. The control unit (ST) now also supplies a reference voltage at the fourth control terminal (G4) of the fourth transistor (T4) when the first LED (LED1) is switched off, if this transistor is to be switched on to switch off the first LED (LED1) more quickly, so that the fourth transistor (T4) also acts as a current source when switched on. This reliably prevents an overload of the first LED (LED1) if, for example, the second positive supply voltage (VCC2) exhibits a voltage spike within the control range of the fourth transistor (T4) for whatever reason. Figure 19 Fig. 19 shows the simplest variant with a supply from a common voltage source with a basic supply voltage (VCC), which could, for example, be the power supply from the vehicle's electrical system. A third voltage regulator (SR3) generates a third supply voltage (VCC3) from the basic supply voltage (VCC). A second voltage regulator (SR2) generates a second supply voltage (VCC2) from the basic supply voltage (VCC). The second analog multiplexer, already described above, consisting of the eighth transistor (T8) and the twelfth transistor (T12), switches between the third supply voltage (VCC3) and the second supply voltage (VCC2) depending on the two control signals (G13, G12). These two control signals are generated by the control unit (ST) together with the control signals (G1, G2, G3, G4) for the H-bridge control of the H-bridge (H). The third supply voltage (VCC3) is intended for quasi-continuous operation (QDB), in which the first LED (LED1) is used as the light source of a lighting device, for example, a vehicle headlight (SW). In the example shown in Fig. 19, the third supply voltage (VCC3) is supplied via the switched-on twelfth transistor (T12) and the switched-on third transistor (T3) in this quasi-continuous operation (QDB). The LED current is carried off via the switched-on second transistor (T2) in this quasi-continuous operation (QDB). If necessary, the second transistor (T2) can again be operated as a current source by the control unit (ST) by means of a reference voltage on the control line (G2) of the second transistor (T2). In this state, the eighth transistor (T8), the first transistor (T1), and the fourth transistor (T4) are switched off. The second supply voltage (VCC2) is intended for pulsed operation (GPB). The magnitude of the voltage value of the second supply voltage (VCC2) is preferably higher than the magnitude of the voltage value of the third supply voltage (VCC3). In pulsed operation (GPB), if the first LED (LED1) is to be switched on quickly, the eighth transistor (T8), the third transistor (T3), and the second transistor (T2) are switched on. During this switch-on process, the second transistor (T2) can optionally be used as a current source again. The twelfth transistor (T12), the fourth transistor (T4), and the first transistor (T1) are switched off in this operating state of the H-bridge. In pulsed operation (GPB), if the first LED (LED1) needs to be quickly switched off, the first transistor (T1) and the fourth transistor (T4) are switched on. During this switch-off process, the fourth transistor (T4) can optionally be used as a current source again to prevent overloading the first LED (LED1). The twelfth transistor (T12), the eighth transistor (T8), the third transistor (T3), and the second transistor (T2) are switched off or are currently switching off in this operating state of the H-bridge (H). Figure 20 Fig. 20 corresponds to Fig. 19 except that the eighth transistor (T8) has been omitted. The analog multiplexer for switching the supply voltage between the third supply voltage (VCC2) and the second supply voltage (VCC2) is therefore no longer placed on top of the H-bridge (H) as in Fig. 19, but has become part of the H-bridge (H) by connecting the twelfth transistor (T12) in parallel with the third transistor (T3). In this example, the analog multiplexer consists of the third transistor (T3) and the twelfth transistor (T12). The third supply voltage (VCC3) is again intended for quasi-continuous operation (QDB), in which the first LED (LED1) is used as the light source of a lighting device, for example, a vehicle headlight (SW). In the example shown in Fig. 19, the third supply voltage (VCC3) is supplied via the switched-on twelfth transistor (T12) in this quasi-continuous operation (QDB). The LED current is carried away via the switched-on second transistor (T2) in this quasi-continuous operation (QDB). If necessary, the second transistor (T2) can again be operated as a current source by the control unit (ST) by means of a reference voltage on the control line (G2) of the second transistor (T2). In this state, the third transistor (T3), the first transistor (T1), and the fourth transistor (T4) are switched off. The second supply voltage (VCC2) is again intended for pulsed operation (GPB). The magnitude of the voltage value of the second supply voltage (VCC2) is preferably higher than the magnitude of the voltage value of the third supply voltage (VCC3). In pulsed operation (GPB), if the first LED (LED1) is to be switched on quickly, the third transistor (T3) and the second transistor (T2) are switched on. During this switch-on process, the second transistor (T2) can optionally be used as a current source again. The twelfth transistor (T12), the fourth transistor (T4), and the first transistor (T1) are switched off in this operating state of the H-bridge (H). In pulsed operation (GPB), if the first LED (LED1) needs to be quickly switched off, the first transistor (T1) and the fourth transistor (T4) are switched on. During this switch-off process, the fourth transistor (T4) can be used as a current source to prevent overloading the first LED (LED1). The twelfth transistor (T12), the third transistor (T3), and the second transistor (T2) are switched off or are currently switching off in this operating state of the H-bridge. Figure 21 Fig. 21 shows a particularly simple version of the proposed device. The light source, the first LED (LED1), is supplied with electrical energy via an H-bridge (H) consisting of a first half-bridge (HB1: T1, T2) and a second half-bridge (HB2: T3, T4). The light source, the first LED (LED1), is connected at its first terminal, the cathode (K) of the first LED (LED1), to the output of the first half-bridge (HB1: T1, T2). The light source, the first LED (LED1), is connected at its second terminal, the anode (A) of the first LED (LED1), to the output of the second half-bridge (HB2: T3, T4).The first half-bridge (HB1: T1, T2) and the second half-bridge (HB2: T3, T4) are supplied with electrical energy via a common positive supply voltage, the first positive supply voltage (VCC1), and a single common negative supply voltage, the reference potential (GND), which can be passed on to the light source, the first LED (LED1). An exemplary first voltage regulator (SR1) generates the first positive supply voltage (VCC1) from the total positive supply voltage (VCC). This can also be a linear regulator. Preferably, the first positive supply voltage (VCC1) as the output voltage of the voltage regulator (SR1) in this example depends on whether the state of the overall system is in quasi-continuous operation (QDB) for illumination purposes or in pulsed operation (GPB) for emitting light pulses for measurement purposes or for data transmission. Figure 22 The state diagram of Fig. 22 corresponds to the state diagram of Fig. 9, but the state diagram has now been modified for the operation of the exemplary modified H-bridge (H) of Fig. 16, Fig. 17, Fig. 18, Fig. 19, Fig. 20 to Fig. 21. The state diagram is described in exemplary connection with Fig. 20 and Fig. 21 as possible forms of the proposed H-bridge (H). The switching states of the transistors (T1, T2, T3, T4, T12) are monitored and controlled by the control unit (ST). The overall device may include measuring instruments (HCV, HCI1, HCI2, HCI3, HCI4, HCI12) to determine the switching state of the transistors (T1, T2, T3, T4, T12). These measuring instruments transmit their results either to the aforementioned computer system (µC) that controls the control unit (ST), where the results are evaluated, and / or directly to the control unit (ST), whose output signals then depend, at least partially, on these results. The overall device may also include measuring instruments for detecting the partial currents in the half-bridges (HB1, HB2) of the H-bridge (H). In particular, it can have a first measuring device (Rs1) in the first half-bridge (HB1: T1, T2) that detects the electric current through a part of the first half-bridge (HB1: T1, T2) and converts it into an electrical voltage, which is then converted by a measuring device not shown in the figures into a measured value for this electric current, which is then made available to the processing unit (µC) or the control unit (ST) for controlling the H-bridge or the charge pumps (LPPA, LPPB, LPMA, LPMB) or the voltage converters (SVPA, SVPB, SVMA, SVMB) or the voltage regulators (SR1, RS2) or the control unit (ST). In particular, it can have a second measuring device (Rs2) in the second half-bridge (HB2: T3, T4) that detects the electric current through a part of the second half-bridge (HB2: T3, T4) and converts it into an electrical voltage, which is then converted by a measuring device not shown in the figures into a measured value for this electric current, which is then made available to the processing unit (µC) or the control unit (ST) for controlling the H-bridge or the charge pumps (LPPA, LPPB, LPMA, LPMB) or the voltage converters (SVPA, SVPB, SVMA, SVMB) or the voltage regulators (SR1, RS2) or the control unit (ST). The H-bridge (H) can preferably be operated in a first intermediate state (Z). In this intermediate state, the first transistor (T1), the second transistor (T2), the third transistor (T3), the fourth transistor (T4), and the twelfth transistor (T12) are switched off. The intermediate state (Z) is intended for quasi-continuous operation (QDB) when the first LED (LED1) is used as the light source of a lighting device, e.g., a headlight of a motor vehicle (MV). The H-bridge (H) can preferably be operated in an intermediate state (PZ) of pulsed operation (GPB). In this intermediate state (PZ) of pulsed operation (GPB), the first transistor (T1), the second transistor (T2), the third transistor (T3), the fourth transistor (T4), and the twelfth transistor (T12) are all switched off. However, the intermediate state (PZ) of pulsed operation (GPB) is intended for pulsed operation (GPB) when the first LED (LED1) is used as a measuring element in a sensor device, e.g., a vehicle distance measuring device. The distinction between the first intermediate state (Z) and this intermediate state (PZ) of pulsed operation (GPB) is important when only one H-bridge with four transistors (T1, T2, T3, T4) according to Fig. 1 and only one voltage regulator are to be used (see Fig. 21).In this case, after switching in any direction between pulsed operation (GPB) and quasi-continuous operation (QDB) in the example of Fig. 20, the voltage at the fifth terminal (5) of the third transistor (T3) and at the first terminal (1) of the first transistor (T1) must first be recharged from the voltage value of a first supply voltage (VCC1) to the voltage value of a third supply voltage (VCC3). This typically takes some time, as the voltage regulator (SR2) must first adjust to the new supply voltage. Therefore, it is better to use two voltage regulators, a first voltage regulator (SR1) and a third voltage regulator (SR3), which supply the first supply voltage (VCC1) and the third supply voltage (VCC3), and then switch between these supply voltages (VCC1, VCC3) using an analog multiplexer (T3, T12), which is preferably part of the H-bridge (H). The second overall state, the "PAn" state, is maintained during light pulse operation for no longer than a switch-on time (τpp), which is preferably shorter than the charge carrier lifetime (τ), since, according to the technical teaching proposed here, the control is achieved with an increased operating voltage in the forward direction of the LEDs during this light pulse operation. Similarly, the third overall state, the "PAus" state, is also maintained for no longer than a clearing time (τpn), where the clearing time (τpn) is shorter than the charge carrier lifetime (τ), since, according to the technical teaching proposed here, the control is achieved with an increased operating voltage in the reverse direction of the LEDs during this light pulse operation. It is of particular importance that the space charge region of the LEDs must not be discharged. The switch-on time (τpp) must be shorter than the charge carrier lifetime (τ). In quasi-continuous operation (QDB), the H-bridge (H) can switch from the intermediate state (Z) to the "BAn" state (BAn) and back. This switch is controlled by the control device (ST). In this "BAn" state (BAn), the first LED (LED1) is more or less continuously energized as the light source of a lighting device. The first transistor (T1), the fourth transistor (T4), and the third transistor (T3) are switched off. The twelfth transistor (T12) connects the first LED (LED1) to the first voltage source (SR1) and thus to the first supply voltage. The first voltage source (SR1) is therefore designed for continuous operation. Its time constants can be longer, while it must be able to withstand the resulting power dissipation for extended periods. The second transistor (T2) is also switched on. Preferably, however, it operates as a current source.In this case, it is able to control the energy consumption of the first LED, since it can then regulate the current through the first LED (LED1). It was therefore recognized during the development of the proposal that it is particularly advantageous if the proposed H-bridge includes a current source or a current source transistor (T2). In quasi-continuous operation (QBD), the H-bridge (H) can switch from the intermediate state (Z) to the optional state "K" and back. In quasi-continuous operation (QBD), the H-bridge (H) can switch from the "PAus" state (PAus) to the optional "k" state (k) and back. In pulsed operation (GPB), the H-bridge (H) can also switch from the "PAus" state (Paus) to the optional "k" state (k). In pulsed operation (GPB), the H-bridge (H) can also switch from the intermediate state for pulsed operation (PZ) to the optional "k" state (k) and back. These transitions are controlled by the control device (ST). In this state (K), the first LED (LED1), acting as the light source of a lighting device, is discharged more or less continuously. The "k" state (k) is optional because no current flows through the first LED (LED1) even in the intermediate state (Z). The “k” state (k) can be realized in two different ways.The basic principle is to reduce the voltage drop across the first LED (LED1) to zero. This requires short-circuiting the first LED (LED1). In the example shown in Fig. 20, this is preferably done via one of the supply voltages, either the second positive supply voltage (VCC2) or the negative supply voltage (GND). In the first case, as shown in Fig. 20, the first transistor (T1) and the third transistor (T3) are electrically conducting. The fourth transistor (T4), the second transistor (T3), and the twelfth transistor (T12) are blocked and therefore do not conduct electricity. In this case, the short circuit of the first LED (LED1) occurs via the second positive supply voltage (VCC2). In the second case, as shown in Fig. 20, the second transistor (T2) and the fourth transistor (T4) are electrically conducting. The first transistor (T1), the third transistor (T3), and the twelfth transistor (T12) are blocked and therefore do not conduct electricity. In this case, the short circuit of the first LED (LED1) occurs via the negative supply voltage (GND). In quasi-continuous operation (QDB), the H-bridge (H) can switch from the intermediate state (Z) to the optional "BAus" state (BAus) and back. This switch is controlled by the control device (ST). In this "BAus" state (BAus), the first LED (LED1) is operated more or less permanently in reverse bias as the light source of a lighting device. The "BAus" state (BAus) is optional because no current flows through the first LED (LED1) even in the intermediate state (Z), and therefore it cannot remain illuminated continuously. The "PAus" state is achieved by operating the first LED (LED1) in reverse bias. For this purpose, in the "PAus" state, with reference to Fig. 20, the first transistor (T1) and the fourth transistor (T4) are connected in a conducting state. The twelfth transistor (T12), the third transistor (T3), and the second transistor (T2) are, for example, switched off with reference to Fig. 20. The “PZ” state and the intermediate state (Z) form more or less a unit, which is indicated as a dashed bubble. A transition from the "BAus" state to the "PZ" state is optionally possible. Direct transitions from the "k" state to the "BAn" state, or vice versa, are preferably not allowed to prevent crossflows at this point. Direct transitions from the "BAus" state to the "BAn" state, or vice versa, are also preferably not allowed to prevent crossflows at this point. In quasi-continuous operation (QDB), the H-bridge (H) can switch from the intermediate state (Z) to the intermediate state (PZ) for pulsed operation (GPB) and thus to pulsed operation (GPB) and back. This switch from pulsed operation (GPB) to quasi-continuous operation (QDB) and back is, in the example shown in Fig. 21, associated with a recharging of the nodes to the new operating voltage. In pulsed operation (GPB), the H-bridge can switch from its intermediate state (PZ) for pulsed operation (GPB) to the "PAn" state. In this state (PAn), the first LED (LED1) should be switched on as quickly as possible. To achieve this, the first LED (LED1) is connected to the highest possible operating voltage as quickly as possible in this state to flood the PN junctions of the first LED (LED1) with charge carriers as rapidly as possible. In the example shown in Fig. 20, this means that of the transistors (T1, T2, T3, T4, T12), which were all previously switched off, the third transistor (T3) and the second transistor (T2) are now switched on. While the switch from the "PAn" state to the intermediate state (PZ) for pulsed operation (GPB) is theoretically possible, it is not the preferred method.Rather, the H-bridge preferentially transitions to an intermediate state (PQZ) with a maximized cross-current to remove the charge carriers from the H-bridge and the first LED (LED1) as quickly as possible. The goal here is to clear the first LED (LED1) and the switching-off transistors (in the example of Fig. 20, the second transistor (T2) and the third transistor (T3)) of charge carriers as quickly as possible. Since the switching-off transistors (in the example of Fig. 20, the second transistor (T2) and the third transistor (T3)) require some time to switch off when transitioning from the "PAn" state to the "QPZ" state, it is advantageous to allow a cross-current to flow through the H-bridge to remove these charge carriers. This achieves two effects: Firstly, the switching-off transistors (in the example, the second transistor T2) are switched on more quickly by the switching-on transistor (in the example of Fig. 20, the second transistor T3).In the example of Fig. 20, the second transistor (T2) and the third transistor (T3) discharge quickly. As a result, the first transistor (T1) also absorbs a large portion of the current that the switching-off second transistor (T2) would otherwise supply to the first LED (LED1). Similarly, in the example of Fig. 20, the fourth transistor (T4) also absorbs a large portion of the current that the switching-off third transistor (T3) would otherwise supply to the first LED (LED1). Secondly, this leads to a faster polarity reversal and thus discharge of the first LED (LED1). It is therefore advantageous to maximize the permissible cross-current during the switch-off of the switching-off transistors (in the example of Fig. 20, the second transistor (T2) and the third transistor (T3)) during the transition from the "PAn" state to the "PAus" state via the "QPZ" intermediate state described here, up to the thermal limit. This means that the transition from the "PAn" state to the "PAus" state preferably occurs via the "PQZ" state described here, whereby, upon entering the "PAus" state, a cross-current is briefly permitted that is larger than the cross-current in the "PZ" or "PAus" state. In order to achieve the aforementioned cross-current maximization at the beginning in the "PAus" state, it is particularly advantageous to be able to capture the essential parameters of the energy loss in the transistors (T1, T2, T3, T4).Since the behavior of the transistors (T1, T2, T3, T4) is generally known, it is useful to calculate the respective energy output based on the voltage drops. The axial current of the H-bridge (H) through the first LED (LED1) can usually be deduced from the voltage drop across the first LED (LED1). In this context, it can be useful to measure the current precisely using two shunt resistors (RS1, RS2), for example, in the ground lines of the H-bridge (H) (see Fig. 23), rather than simply estimating it from the voltage drop across the transistors (T1, T2, T3, T4). Since the function of the transistors (T1, T2, T3, T4) is different, the first transistor (T1) of the H-bridge (H) is typically not the same as the third transistor (T3) of the H-bridge (H), and the second transistor (T2) of the H-bridge (H) is typically not the same as the fourth transistor (T4) of the H-bridge (H).The precise dimensions will be determined by a person skilled in the art through calculation and simulation, taking into account the first LED (LED1) used and the layout of the typically employed printed circuit board. The control of the cross-currents is preferably achieved by controlling the voltage of the voltage regulators (SR1, SR2) and the switching-on and switching-off times of the transistors (T1, T2, T3, T4). The actual values ​​used for such control can include the voltage across the first LED (LED1), the voltage drops across the transistors (T1, T2, T3, T4), and, if applicable, additional measured values ​​for the current through the respective half-bridges (HB1: T1, T2; HB2: T3, T4) (e.g., the voltage drop across shunt resistors (Rs1, Rs2)), as well as the voltage drops across the transistors (T1, T2, T3, T4) and the first LED (LED1). Furthermore, it can be useful to equip the transistors (T1, T2 / T3, T4) for pulsed operation (GPB) as well as the transistors (T2, T3) for quasi-continuous operation (QDB) with one or more thermocouples that monitor the transistors during operation. Their parameters can also be used for control. The "PAus" state describes another overall state of the device, in which the second transistor (T2), the third transistor (T3), and the twelfth transistor (T12) (exemplary with reference to Fig. 20) are switched off. The first transistor (T1) and the fourth transistor (T4) are conducting. The LED (LED1) does not emit light and is reverse-biased. Figure 23 Fig. 23 corresponds to Fig. 20 except that two shunt resistors, a first shunt resistor (Rs1) and a second shunt resistor (Rs2), are shown. These shunt resistors (Rs1, Rs2) can be used to determine the current through the respective half-bridge (HB1, HB2) of the H-bridge (H) by measuring the voltage drop across them. To determine the current through the second transistor (T2), the voltage between the fourth terminal (4) of the second transistor (T2) and the negative supply voltage (GND) is preferably measured. Given a known value of the first shunt resistor (Rs1), the current through the second transistor (T2) can then be derived from this measured voltage. To determine the current through the fourth transistor (T4), the voltage between the eighth terminal (8) of the fourth transistor (T4) and the negative supply voltage (GND) is preferably measured. Given a known value of the second shunt resistor (Rs2), the current through the fourth transistor (T4) can then be derived from this measured voltage. The measured values ​​thus acquired are particularly preferred for the control of cross currents, especially in the “QPZ” state or at the beginning of the “PAus” state, or for stabilizing the color temperature of the emission of the first LED (LED1) in the “BAn” state in quasi-continuous operation (QDB). Figure 24 corresponds to Fig. 15 with the exemplary difference that an internal construction of the H-bridge corresponds, for example, to Fig. 15 and where the energy reserves (C_LPPB, C_LPPA, C_LPMB, C_LPMA) of the charge pumps (LPPB, LPPA, LPMB, LPMA) are shown. Instead of charge pumps (LPPB, LPPA, LPMB, LPMA), voltage boost converters (SVPB, SVPA, SVMB, SVMA) or similar devices can also be used, which increase the supply voltage relative to the magnitude of the respective positive or negative supply voltage. The reference point for the magnitude increase is the average voltage between the positive and negative supply voltages. The energy reserves of the voltage converters (SVPB, SVPA, SVMB, SVMA) can also be inductors (L_SVPB, L_SVPA, L_SVMB, L_SVMA) or similar devices. Figure 25 This corresponds to Fig. 15 with the exemplary difference that, for example, a first H-bridge control unit (HC1) is provided which measures the light emission of the light source, here the exemplary first LED (LED1), by means of a light-sensitive sensor, here for example a first photodiode (PD1), and thus allows for adjustment of the control, in particular by adjusting the charge pump voltage of the charge pumps (LPPB, LPPA, LPMB, LPMA) or voltage converters (SVPB, SVPA, SVMB, SVMA) or the voltage regulators (SR1, SR2) in the form of the bias voltage of the energy reserves (C_LPPB, C_LPPA, C_LPMB, C_LPMA) of the charge pumps (LPPB, LPPA, LPMB, LPMA) or by adjusting the voltage converter voltage of the voltage converters (SVPB, SVPA, SVMB, SVMA), e.g.The current through the energy reserves (L_SVPB, L_SVPA, L_SVMB, L_SVMA) of the voltage converters (SVPB, SVPA, SVMB, SVMA), if these energy reserves are inductors, can be measured by varying the dwell times in the states "PAN", "PAUS", and "PQZ". Furthermore, the current through the first LED (LED1) can be detected via shunt resistors (Rs1, Rs2) and regulated in pulsed operation (GPB) depending on the state (PAN, PAUS, PQZ, Z) of the H-bridge (H). In quasi-continuous operation (QDB), where the first LED (LED1) is used, for example, as the light source of a headlight (SW), the brightness of the first light source (LED1) can be detected and regulated by the first photodiode (PD1). For this purpose, the control unit (ST) controls the H-bridge (H) in such a way that the first LED (LED1) is preferably driven with a PWM modulation. Its amplitude is shown in the example in Fig.23. The voltage value of the third supply voltage (VCC3) relative to the negative supply voltage (GND) is essentially determined by the voltage losses due to the turn-on resistances of the transistors (T2, T12) and the shunt resistor (Rs1). This voltage amplitude and the average time-based turn-on density (e.g., the duty cycle) then provide two parameters for adjusting the color temperature and brightness. The measurement of the light emission of the light source, the first LED (LED1), can preferably be performed by detecting stray light (SL) falling on the first photodiode (PD1). Since light from outside typically enters the headlight (SW) through the optics (OP), it is advantageous to use the modulation of the light, e.g., by the applied PWM, to separate the ambient light signal from the useful signal in the H-bridge control unit (HC1) or in the processing unit (µC) through signal processing.This separation via signal processing can be achieved, for example, by creating a cross-correlation between the received signal of the photodiode (PD1) or a signal derived from it, e.g., by filtering, and a synchronization signal (sync) corresponding to the transmitted signal of the light source. It is then advantageous if, for example, the processing unit (µC) samples the first measurement signal (MS1) of the first H-bridge control unit (HC1) and multiplies it by the sampled drive signal for the PWM modulation. Since the PWM frequency is known, it is then advantageous to remove all frequencies higher than half the PWM frequency from the spectrum using a low-pass filter. Typically, a DC signal then remains, e.g., for the brightness of the first LED (LED1). Figure 26 This corresponds to Fig. 25 with the exemplary difference that, by way of example, further light sources (LED2...n) are provided which emit light unpulsed for illumination purposes, whereby a blocked wavelength range (GWB) is masked out by a filter (F1). In the example of Fig. 26, the device has a further reflector (RF2) and a second optic (OP2) for collecting and extracting the spotlight light (SWL) generated by the further light sources (LED2...n). Figure 27 Fig. 27 corresponds to Fig. 26, except that for clarity, a measuring device (MV) is now shown, which allows, for example, the determination of the light travel time or other information such as the reflectivity of an object (O) from the reflected light pulses (RLP). The light pulses (LP) emitted by the first LED (LED1) are reflected by an object (O) not shown, for example, a vehicle traveling ahead, and return as reflected light pulses (RLP) to the proposed device, for example, a proposed headlight (SW). There, they pass, for example, through a third optic (OP3) and a preferred third optical filter (F3), which is preferably designed to be complementary to the first optical filter (F1). This means that the first filter (F1) preferably blocks the spectrum of the further light sources (LED2...n) in the generated spotlight light (SWL) the wavelength range (VWB) used for the measurement is filtered or at least attenuated to such an extent that no unnecessary additional load is generated. In this respect, the first filter (F1) is optional. The first LED (LED1) preferably emits in the wavelength range (VWB) used for the measurement. The third filter (F3) then preferably separates the wavelength range (VWB) used for the measurement from the entire transmitted optical spectrum. The reflected light pulses (RLP) preferably pass through the third filter (F3) undamped and are detected by the measuring sensor, preferably a measuring photodiode (MD). The measuring device (MV) determines a measured quantity from the detected signal of the measuring diode (MD) and transmits this as a third measurement signal (MS3) to the computer system (µC). This measuring device (MV) can also include more than one measuring diode (MD). A particularly preferred measuring diode is known from DE 10 2009 020 218 B3.Particularly preferably, several such measuring diodes are arranged in a diode array. The third optic (OP3) is then preferably designed to generate an image of the reflected light pulse (RLP) coming from the object on the diode array (MD). The control unit (ST) then generates the necessary control signals, e.g., according to DE 10 2008 018 718 B4. The gate signals provided therein, which switch the diodes (MD) of the diode array between light-sensitive and insensitive (in the literature these are also referred to as shutter signals), are then switched such that the diodes (MD) can preferably only be switched to be light-sensitive in the states "k", "PAn", "PZ", "PAus", and "PQZ". Most preferably, the diodes are switched to be insensitive in the states "Z", "BAn", and "BAus", so that they do not collect any light in these states. In this way, distance and brightness information can be obtained for each pixel. Figure 28 Fig. 28 corresponds to Fig. 27 with the difference that a compensation transmitter (K) is now provided, which is driven complementarily to the first LED (LED1), whereby a more or less uniform illumination of the photodiode (MD) is achieved by controlling the amplitude and phase of the drive signal to the compensation diode (K). A corresponding measurement method is known, for example, from EP 2 783 232 B1. Figure 29 This corresponds to Fig. 15 with the exemplary difference that, by way of example, a first LED (LED1a), controlled by an exemplary first H-bridge (H), and a second LED (LED1b), controlled by an exemplary second H-bridge (H'), are provided, thus enabling the emission of colored light pulses (FLP). A first LED (LED1a) is controlled by a first H-bridge (H) and emits light pulses (LP) and / or light pulse sequences (LPF) in a first wavelength range (WB1), i.e., for example, with a first color. The first H-bridge (H) is controlled by the control unit (ST). A second LED (LED1b) is controlled by a second H-bridge (H') and also emits light pulses (LP) and / or light pulse sequences (FLP) in a second wavelength range (WB2), i.e., for example, with a second color.The first wavelength range (WB1) preferably differs from the second wavelength range (WB2) at least in the spectral intensity profile of the respective LED. Thus, the first color is preferably different from the second color. The second H-bridge (H') is also controlled by the control unit (ST). The mixed scattered light (SL1, SL2) from the first LED (LED1a) and the second LED (LED1b) is received here, by way of example, by a first photodiode (PD1) and a second photodiode (PD2). The first photodiode (PD1) and the second photodiode (PD2) are intended to have different spectral wavelength ranges (WB1, WB2) in which they are differently sensitive to the light from the first LED (LED1a) and the light from the second LED (LED1b). This difference should be chosen such that it is possible to infer the luminous intensity of the first LED (LED1a) and the second LED (LED1b).For example, it would be preferable for the first photodiode (PD1) to be exclusively sensitive to the light from the first LED (LED1a) and the second photodiode (PD2) to the light from the second LED (LED1b). This setup would then allow colored light pulses (FLP) to be generated using light pulses (LP) from several light sources (LED1a, LED1b), for example, of different colors, whose total intensity (total luminous flux) remains constant for the duration of the colored light pulse (FLP), and in which only the color, i.e., the hue, is pulsed.A constant total luminous flux is understood to mean a change in the total luminous flux of less than 10% within a period of the duration of the light pulse, while the ratio (division of the luminous flux values) of the emitted luminous fluxes in a first wavelength range (WB1) of the emitted light to a second wavelength range (WB2) of the emitted light changes relative to each other by more than 10% during this period. Figure 30 This corresponds to Fig. 15 with the exemplary difference that it is a proposed RGB spotlight (SW) and that, by way of example, a first LED (LED1a) driven by an exemplary first H-bridge (H), a second LED (LED1b) driven by an exemplary second H-bridge (H'), and a third LED (LED1c) driven by an exemplary third H-bridge (H'') are provided, which opens up the possibility of emitting color pulses (FLP) and simultaneously emitting color-defined light, for example also white light, for illumination purposes in the entire RGB color spectrum. Figure 31 This corresponds to Fig. 25, with the exemplary difference that an exemplary structurable filter, here in the form of an LCD filter (LCD), is inserted into the beam path, for example within the optics (CL, PL), and projected. This enables the projection of structures as a mask. It may be useful, for example, to restrict the measurement to specific areas. Figure 32 This corresponds to Fig. 25 with the exemplary difference that an exemplary micromirror array (DLP), here in the form of an LCD filter, is inserted into the beam path and spatially and / or temporally modulates the light beam cross-section. Figure 33 This corresponds to Fig. 25 with the exemplary difference that an exemplary structurable filter, here in the form of an LCD filter (LCD), is inserted into the beam path exemplarily behind the optics (OP) and is projected as a shadow mask. Figure 34 This figure shows exemplary positions of devices according to this proposal on an exemplary motor vehicle (in the form of an exemplary passenger car). Reference is made to the list of reference symbols. The proposed device can be installed at the front in the daytime running lights (FST1, FST2), the low beam headlights (FAS1, FSA2), and the high beam headlights (FSF1, FSF2). The fog lights (NL1, NL2) are also located there. Fog lights are a possibility. The turn signals (BL1, BL2) at the corners of the vehicle could be designed according to this proposal. Warning lights and the blue flashing lights of emergency services, etc., could be positioned on the roof. For example, warning lights (TWL1, TWL2) for vehicles in the blind spot, which are typically located on the rearview mirrors, are suitable for use on the side. At the rear of the vehicle, the brake lights (BRL1, BRL2), the reversing lights (RFL1, RFl2), the rear fog lights (NRL1, NRL2) and the rear light (RL1, RL2) are particularly suitable for a design in accordance with this proposal. Decorative lights (ZL1, ZL2) around the entire vehicle are suitable for a design in accordance with this proposal. Figure 35 This diagram illustrates an example of communication between a vehicle equipped with a proposed headlight and a traffic infrastructure device, in this case, a traffic light. For example, assume that the vehicle's right headlight is designed as proposed and can emit pulsed light. The vehicle can then send information to the traffic infrastructure device, in this case, a traffic light, by modulating the pulse interval in pulsed mode. The traffic light receives this pulse sequence via an optical receiver. This can, for example, cause the traffic light controller to change its state, such as switching from red to green at night if no other request is present. Conversely, the traffic light can also send data to the vehicle using an optical pulse sequence.If the pulses are short enough and not too frequent, and if the spectrum generated by the pulsing does not exhibit any modulation frequencies perceptible to the human eye, then these are no longer readily perceptible to a human observer. The proposed devices are therefore intended to... Quasi-continuous operation should preferably be shorter than 10µs, better shorter than 3µs, better shorter than 2µs, better shorter than 1µs, better shorter than 500ns, better shorter than 200ns, better shorter than 100ns, better shorter than 50ns, better shorter than 20ns, better shorter than 10ns, better shorter than 5ns, better shorter than 4ns, better shorter than 2ns, better shorter than 1ns, better shorter than 500ps, better shorter than 200ps, better shorter than 100ps, better shorter than 50ps, better shorter than 20ps, better shorter than 10ps, better shorter than 5ps, better shorter than 2ps, better shorter than 1ps, exit and then return to quasi-continuous operation. In quasi-continuous operation, the energy supply is preferably provided by voltage converters with a preferably lower maximum light output than in pulsed operation with a preferably massively increased pulsed light output and a preferred energy supply from charge pumps. Figure 36 shows an exemplary communication between a first vehicle (Kfz) and a second vehicle (Kfz2), each equipped with a proposed headlight (SW), whereby they a) determine the distances to each other a1) actively and a2) passively using these headlights (SW) and b) exchange data. For example, the first vehicle (V1) can determine its distance to the second vehicle (V2) ahead using a proposed device (e.g., Fig. 28). Simultaneously, the first vehicle (V1) can use the light pulses (LP) of these measurement signals to transmit information to the second vehicle (V2) ahead, such as its own speed, the measured distance, and its acceleration status (brake pedal engaged or not, etc.), or even its own position determined by other means. Other data transmission methods are also conceivable. It is therefore proposed to utilize the headlight of the first vehicle (V1) in three different ways. 1. as a lighting device 2. as a measuring device (e.g. for measuring distance) 3. as a transmitter of a data interface It is particularly preferred that at least one LED (LED1) of the headlight (SW) is used simultaneously for these three purposes. Furthermore, an LED (LED1) within the headlight (SW) can also be used as a receiver. However, this requires that no light is emitted during the reception period to prevent overloading. In this case, the LED (LED1) would be used four times. Figure 37 Fig. 37 shows the H-bridge of Fig. 1, where the first positive supply voltage (VCC1) of the H-bridge of Fig. 1 and the second positive supply voltage (VCC2) of the H-bridge of Fig. 1 are equal to the total positive supply voltage (VCC), and where the first negative supply voltage (GND1) of the H-bridge of Fig. 1 and the second negative supply voltage (GND2) of the H-bridge of Fig. 1 are equal to the total negative supply voltage (GND). Figure 38 Fig. 38 shows the actual H-bridge (H) with the first half-bridge (HB1) from the series connection of the first transistor (T1) and the series connection of the second transistor (T2) and with the second half-bridge (HB2) from the series connection of the third transistor (T3) and the series connection of the fourth transistor (T4). Figure 39 Fig. 39 corresponds to Fig. 27 with the difference that, instead of a single sensor (MD), a two-dimensional arrangement of time-controlled light-sensitive sensors (TOFIMG) is now used for the detection of the light pulses (LP) or colored light pulses (FLP). In this context, reference is made here to documents DE 10 2008 018 718 B4 and DE 10 2009 020 218 B3. glossary LED Light-emitting diode or LED. For the purposes of this disclosure, this can also refer to an interconnection of several light-emitting diodes and other components which, as a group, have the same light emission function when a forward voltage is applied as a single light-emitting diode, whereby the forward voltage of such a group may differ. Preferably, this is a series connection (LED chain) of individual light-emitting diodes. Laser diodes are also included as LEDs for the purposes of this disclosure. LIDAR Ladar (short for light detection and ranging), also known as laser detection and ranging, is a method very similar to radar for optical distance and velocity measurement, as well as for remote sensing of atmospheric parameters. Instead of radio waves, radar uses laser beams. Flash LiDAR In flash lidar, a single light pulse is emitted, and the time-of-flight (TOF) of this light pulse is measured from the transmitter, via reflection from an object (O), back to a receiver, with direction resolution, for example, using a so-called TOF camera or time-of-flight camera. This allows an environmental map (UK) to be created without the need for moving parts. TOF distance measurement In TOF distance measurement, the transit time of a light pulse (LP) or colored light pulse (FLP) is measured, and a distance (d, d1, d2, d3) is calculated from this if the speed of a radiation packet is known. 3D Imaging 3D imaging refers to the creation of an image that, like a normal camera, contains brightness information for each camera pixel, but also distance information for each camera pixel. Such cameras preferably use time-of-flight (TOF) measurement. For example, German patent DE 10 2009 020 218 B3 is known in connection with such time-of-flight measurement. Optical Data Link Optical data link refers to a data connection that is established using a modulated light beam as a transmission medium. Car2Car Communication Car2Car communication refers to data communication between two vehicles (vehicle1, vehicle2). charge pump A charge pump is a device typically part of the integrated driver circuit used to drive the first LED (LED1) via the proposed H-bridge (H). The term "charge pump" encompasses several different electrical circuits that either increase the magnitude of an electrical voltage or reverse the polarity of DC voltages. For the purposes of this disclosure, this refers to further lowering the negative supply potential (GND) or further increasing the positive supply voltage (VCC). The output voltage of a charge pump is typically a DC voltage. If the input voltage is also a DC voltage, the charge pump is classified as a DC-DC converter. A key characteristic of charge pumps is that they do not use magnetic components such as coils or transformers. Charge pumps transport electrical charge preferably using electrical capacitors and by periodic switching with switches, thereby generating different electrical output voltages. The process is similar to carrying water in buckets from a low point to a higher point, where it is collected with higher potential energy. Since the first LED (LED1) only pulses, continuous operation is not required, and an external storage capacity can be charged by the respective charge pump between the light pulses being emitted. According to this disclosure, voltage converters can also be used instead of charge pumps. Voltage converter A voltage converter is a device, typically part of the integrated driver circuit used to drive the first LED (LED1) via the proposed H-bridge (H). The term "voltage converter" encompasses several different electrical circuits that either increase the magnitude of electrical voltages or reverse the polarity of DC voltages. For the purposes of this disclosure, this refers to further lowering the negative supply potential (GND) or further increasing the positive supply voltage (VCC). The output voltage of a voltage converter is typically a DC voltage. If the input voltage is also a DC voltage, the voltage converter is classified as a DC-DC converter.A DC-DC converter is an electrical circuit that converts an input DC voltage into a DC voltage with a higher, lower, or inverted voltage level. This conversion is typically achieved using a periodically operating electronic switch and one or more energy storage devices. DC-DC converters are self-commutated power converters. In the field of electrical power engineering, they are also referred to as DC choppers. For the purposes of this disclosure, the energy storage device used for intermediate energy storage is preferably an inductor (inductive converter). Such a DC-DC converter therefore preferably also includes an inductor or a converter transformer. Unlike the capacitance of a charge pump, these are difficult to integrate into an integrated circuit, which is why charge pumps are the focus of this disclosure.In contrast, converters with capacitive storage (capacitive converters) are referred to as charge pumps. Charge pumps are used when either inductors are unavailable—as in integrated circuits—or when so little output power is required that the use of expensive inductors is not worthwhile compared to inexpensive capacitors. Provided the first LED (LED1) is only pulsed, continuous operation is not required, and an external storage capacitor can be charged by the respective charge pump between the emitted light pulses. According to this disclosure, charge pumps can also be used instead of voltage converters.Preferably, voltage converters supply the electrical energy for lighting purposes to the H-bridge, and thus to the light source (LED1), at a lower output voltage than the charge pumps, which, in comparison, generate a preferably higher voltage difference between the light source terminals for a very short time during pulsed operation (GPB). This prevents the light source (LED1) from being energetically overloaded in either quasi-continuous or pulsed operation. In quasi-continuous operation (QDB), this energy supply occurs over a longer period from the voltage converters at lower electrical power, while in pulsed operation (GPB), it is supplied by the charge pumps over a short period at very high electrical power. Since the time spent using the charge pump output power is short, the energy storage capacity of the charge pumps can be limited. wavelength For the purposes of this disclosure, the wavelength of an LED is understood to be the wavelength of the unmodulated light emitted by the LED (LED1) or the light source. When referring to the wavelength of a light source, this means the center wavelength of the emission from the respective light source (LED1). RGB LED An RGB LED is understood to be a group of at least three LEDs of different colors. (See also the definition of LED above.) ADAS ADAS stands for Advanced Driver Assistance Systems. Driver assistance systems are electronic add-ons in motor vehicles designed to support the driver in specific driving situations. Safety aspects are often paramount, but increasing driving comfort is also a key consideration. Improved fuel economy is another important aspect. This disclosure describes how the circuit technology used to control the LEDs of existing lighting systems enables their use in conjunction with ADAS systems, for example, as distance sensors or as a source of an environmental map. IR light IR light means infrared light. In physics, infrared radiation (also called ultra-red radiation) refers to electromagnetic waves in the spectral range between visible light and the longer-wavelength terahertz radiation. Infrared is defined as the spectral range between 10⁻³ m and 7.8 × 10⁻⁷ m (1 mm and 780 nm), which corresponds to a frequency range of 3 × 10¹¹ Hz to approximately 4 × 10¹⁴ Hz (300 GHz to 400 THz). Visible light / visible wavelength range Visible light is the portion of electromagnetic radiation that is visible to the human eye. In the electromagnetic spectrum, the range of visible light spans wavelengths from 380 nm to 780 nm. This corresponds to frequencies of approximately 789 THz to 384 THz. A precise boundary cannot be defined, as the sensitivity of the eye varies depending on the wavelength. The limits of perception do not decrease abruptly, but gradually. For the purposes of this disclosure, 380 nm to 780 nm are considered the wavelength range of visible light. The regions adjacent to visible light, namely infrared (wavelengths between 780 nm and 1 mm) and ultraviolet radiation (wavelengths between 10 nm and 380 nm), are often also referred to as light. This disclosure relates to light sources (LED1) that preferably emit white light. The light sources (LED1) may have laser properties. Data link A data link is a data connection using a carrier of electromagnetic radiation. headlights For the purposes of this disclosure, a headlight is any light fixture with a light source that emits, among other things, pulsed light. Specifically, with regard to a motor vehicle, a headlight is a daytime running light, a low beam headlight, a high beam headlight, a decorative light, a direction indicator, a warning light, a blind spot warning light, a brake light, a reversing light, a taillight, a fog light, a rear fog light, a warning light, a signal light, in particular a police, fire service, or other emergency vehicle blue light or other yellow warning light with or without rotation and with or without flashing function; and with regard to a rail vehicle, a driving light, a decorative light, a warning light, a reversing light, a taillight, a warning light, a signal light.And other lights and application situations included a street light, an advertising installation, a searchlight, a stage light or stage spotlight, a signal light, a traffic light, an emergency light, a workplace light, a room light, a corridor light. vehicles For the purposes of this disclosure, vehicles include all types of vehicles: cars, trucks, motorcycles, rail vehicles, bicycles, all types of sea vehicles such as ships, boats and submarines, aircraft, spacecraft, special vehicles such as tracked vehicles and construction vehicles and machinery, mobile robots, industrial trucks, etc. White appearance of light For the purposes of this revelation, light emission is white if the color temperature is between 3000K and 7000K. Measurement methods Wavelength determination The wavelength of light emission can be determined using a grating spectrometer. capable of light pulsesA light source capable of light pulses (e.g.LED1) within the meaning of this disclosure, if it provides light pulses (LP) of a duration of less than preferably shorter than 10 µs, better shorter than 3 µs, better shorter than 2 µs, better shorter than 1 µs, better shorter than 500 ns, better shorter than 200 ns, better shorter than 100 ns, better shorter than 50 ns, better shorter than 20 ns, better shorter than 10 ns, better shorter than 5 ns, better shorter than 4 ns, better shorter than 2 ns, better shorter than 1 ns, better shorter than 500 ps, ​​better shorter than 200 ps, ​​better shorter than 100 ps, ​​better shorter than 50 ps, ​​better shorter than 20 ps, ​​better shorter than 10 ps, ​​better shorter than 5 ps, better shorter than 2 ps, better shorter than 1 ps, with an amplitude change in luminous power of at least 1%, better at least 2%, better can generate at least 5%, better at least 10%, better at least 20%, better at least 50%, better at least 100%, better at least 200%, better at least 500%, better at least 1000%.A device within the meaning of this disclosure is capable of generating short-pulse light because it can generate light pulses shorter than 5 ns. The duration of the light pulse is defined as the time difference between a first point in time, at which the amplitude change reaches 10% of the maximum amplitude change of the light source during the light pulse (LP), and a second point in time, at which the amplitude change has again fallen back to 10% of the maximum amplitude change of the light source during the light pulse (LP). light pulse A light pulse is an emission of visible light in which the light output is increased or decreased from a first light power to a second light power at a first time point (t1) and returns to the first light power at a second time point (t2) following the first time point (t1). The time difference between the second time point (t2) minus the first time point (t1) is preferably less than 10 µs, better less than 3 µs, better less than 2 µs, better less than 1 µs, better less than 500 ns, better less than 200 ns, better less than 100 ns, better less than 50 ns, better less than 20 ns, better less than 10 ns, better less than 5 ns, better less than 4 ns.The duration of the light pulse is defined as the time difference between a first point in time, at which the amplitude change reaches 10% of the maximum luminaire amplitude change during the light pulse (LP), and a second point in time, at which the amplitude change has fallen back to 10% of the maximum luminaire amplitude change during the light pulse (LP). Color angle light pulse A color-angle light pulse is an emission of visible light in which the average color temperature of the light emission is increased or decreased from a first color temperature to a second color temperature at a first time point (t1) and returns to the first color temperature at a second time point (t2) following the first time point (t1). The time difference between the second time point (t2) minus the first time point (t1) is preferably less than 10 µs, better less than 3 µs, better less than 2 µs, better less than 1 µs, better less than 500 ns, better less than 200 ns, better less than 100 ns, better less than 50 ns, better less than 20 ns, better less than 10 ns, better less than 5 ns, better less than 4 ns. modulated color angle light pulse A colored angle light pulse is an emission of visible light in which the mean color temperature of a first color temperature is increased or decreased to a second color temperature at a first time (t1) and returns to the first color temperature at a second time (t2) following the first time (t1). The mean luminous intensity of a first luminous intensity is increased or decreased to a second luminous intensity at the first time (t1) and returns to the first luminous intensity at the second time (t2).The time difference between the second time point (t2) minus the first time point (t1) is preferably less than 10µs, better less than 3µs, better less than 2µs, better less than 1µs, better less than 500ns, better less than 200ns, better less than 100ns, better less than 50ns, better less than 20ns, better less than 10ns, better less than 5ns, better less than 4ns . Reference symbol list 1 First terminal of the first transistor (T1) of the first half-bridge (HB1) of the first H-bridge (H); 2 Second terminal of the first transistor (T1) of the first half-bridge (HB1) of the first H-bridge (H); 2' Second terminal of the first transistor (T1') of the first half-bridge (HB2) of the second H-bridge (H'); 2'' Second terminal of the first transistor (T1'') of the first half-bridge (HB1) of the third H-bridge (H''); 3 Third terminal of the second transistor (T2) of the first half-bridge (HB1) of the first H-bridge (H); 3' Third terminal of the second transistor (T2') of the first half-bridge (HB1) of the second H-bridge (H'); 3'' Third terminal of the second transistor (T2'') of the first half-bridge (HB1) of the third H-bridge (H''); 4 fourth connection of the second transistor (T2) of the second half-bridge (HB2) of the first H-bridge (H); 5 fifth connection of the third transistor (T3) of the second half-bridge (HB2) of the first H-bridge (H); 6 sixth connection of the third transistor (T3) of the secondHalf-bridge (HB2) of the first H-bridge (H); 6' sixth terminal of the third transistor (T3') of the second half-bridge (HB2) of the second H-bridge (H'); 6'' sixth terminal of the third transistor (T3) of the second half-bridge (HB2) of the third H-bridge (H''); 7 seventh terminal of the fourth transistor (T4) of the second half-bridge (HB2) of the first H-bridge (H); 7' seventh terminal of the fourth transistor (T4') of the second half-bridge (HB2) of the second H-bridge (H'); 7'' seventh terminal of the fourth transistor (T4'') of the second half-bridge (HB2) of the third H-bridge (H''); 8 eighth terminal of the fourth transistor (T4) of the second half-bridge (HB2) of the first H-bridge (H); 9. Ninth connection of the positive charge pump (LPPB) for the rapid extraction of the stored charge carriers or ninth connection of the positive voltage regulator (SVPB) for the rapid extraction of the stored charge carriers, if, instead of the positive charge pump (LPPB), the stored charge carriers are used for the rapid extraction of the stored charge carrierscharge carriers such a positive voltage regulator (SVPB) is used for the rapid extraction of the stored charge carriers, which is part of this disclosure; 10 tenth terminal of the positive charge pump (LPPB) for the rapid extraction of the stored charge carriers or tenth terminal of the positive voltage regulator (SVPB) for the rapid extraction of the stored charge carriers, if such a positive voltage regulator (SVPB) is used for the rapid extraction of the stored charge carriers instead of the positive charge pump (LPPB), which is part of this disclosure; 11 eleventh terminal of the negative charge pump (LPMB) for the rapid extraction of the stored charge carriers or eleventh terminal of the negative voltage regulator (SVMB) for the rapid extraction of the stored charge carriers, if such a negative voltage regulator (SVPB) is used for the rapid extraction of the stored charge carriers instead of the negative charge pump (LPMB), which is part of this disclosure.Voltage regulator (SVPB) is used for the rapid extraction of the stored charge carriers, which is part of this disclosure; 12 twelfth terminal of the negative charge pump (LPMB) for the rapid extraction of the stored charge carriers, or twelfth terminal of the negative voltage regulator (SVMB) for the rapid extraction of the stored charge carriers, if such a negative voltage regulator (SVMB) for the rapid extraction of the stored charge carriers is used instead of the negative charge pump (LPMB) for the rapid extraction of the stored charge carriers, which is part of this disclosure; 13 thirteenth terminal of the positive charge pump (LPPA) for rapid activation, or thirteenth terminal of the positive voltage regulator (SVPA) for rapid activation, if such a positive voltage regulator (SVPA) for rapid activation is used instead of the positive charge pump (LPPA) for rapid activation, which is part of this disclosure; 14 fourteenth15. Connection of the positive charge pump (LPPA) for fast turn-on, or the fourteenth connection of the positive voltage regulator (SVPA) for fast turn-on if such a positive voltage regulator (SVPA) for fast turn-on is used instead of the positive charge pump (LPPA) for fast turn-on, which is part of this disclosure; 16. Connection of the negative charge pump (LPMA) for fast turn-on, or the fifteenth connection of the negative voltage regulator (SVMA) for fast turn-on if such a negative voltage regulator (SVMA) for fast turn-on is used instead of the negative charge pump (LPMA) for fast turn-on, which is part of this disclosure; 17. Connection of the negative charge pump (LPMA) for fast turn-on, or the sixteenth connection of the negative voltage regulator (SVMA) for fast turn-on if such a negative voltage regulator (SVMA) for fast turn-on is used instead of the negative charge pump (LPMA) for fast turn-on, which is part of this disclosure.Voltage regulator (SVMA) is used for fast turn-on, which is part of this disclosure; 17 seventeenth terminal of the ninth transistor (T9) of the first half-bridge (HB1) of the first H-bridge (H); 18 eighteenth terminal of the ninth transistor (T9) of the first half-bridge (HB1) of the first H-bridge (H); 19 nineteenth terminal of the tenth transistor (T10) of the first half-bridge (HB1) of the first H-bridge (H); 20 twentieth terminal of the tenth transistor (T10) of the first half-bridge (HB1) of the first H-bridge (H); 21 twenty-first terminal of the twelfth transistor (T12) of the second half-bridge (HB2) of the first H-bridge (H); 22 twenty-second terminal of the twelfth transistor (T12) of the second half-bridge (HB2) of the first H-bridge (H); 23 twenty-third connection of the eleventh transistor (T11) of the second half-bridge (HB2) of the first H-bridge (H); 24 twenty-fourth connection of the eleventh transistor (T11) of the second half-bridge (HB2) of the first H-bridge (H); 2526 twenty-fifth connection of the fifth transistor (T5) of the first half-bridge (HB1) of the first H-bridge (H); 27 twenty-sixth connection of the fifth transistor (T5) of the first half-bridge (HB1) of the first H-bridge (H); 28 twenty-seventh connection of the sixth transistor (T6) of the first half-bridge (HB1) of the first H-bridge (H); 29 twenty-eighth connection of the sixth transistor (T6) of the first half-bridge (HB1) of the first H-bridge (H); 29 twenty-ninth connection of the eighth transistor (T8) of the second half-bridge (HB2) of the first H-bridge (H); 30 thirtieth connection of the eighth transistor (T8) of the second half-bridge (HB2) of the first H-bridge (H); 31 thirty-first connection of the seventh transistor (T7) of the second half-bridge (HB2) of the first H-bridge (H); 32 Thirty-second terminal of the seventh transistor (T7) of the second half-bridge (HB2) of the first H-bridge (H); a Current waveform during pulse generation with one H-bridge (operating voltage 40V); A Anode of the firstLight-emitting diode (LED1); Aa Anode of the first pulsed LED (LED1a); Ab Anode of the second pulsed LED (LED1b); Ac Anode of the third pulsed LED (LED1c); AMP Traffic light (representing traffic infrastructure equipment or smart home devices); AWB Emitted wavelength range; b Current waveform during pulse generation with a voltage driver (operating voltage 3.3V); BAn On state in quasi-continuous operation (QDB) in which the first LED (LED1) is forward-biased and emits light; BAus Off state in quasi-continuous operation (QDB) in which the first LED (LED1) is reverse-biased; BL Aperture; BRL1 Left brake light; BRL2 Right brake light; c Current waveform during pulse generation with a current driver (operating current 20mA); C_LPMA Energy reserve for the negative charge pump to generate a fast turn-on edge, typically a capacitor; C_LPMB Energy reserve for the negative charge pump for rapid extraction of thestored charge carriers, typically a capacitor; C_LPPA energy reserve for the positive charge pump to generate a fast turn-on edge, typically a capacitor; C_LPPB energy reserve for the positive charge pump to quickly extract the stored charge carriers, typically a capacitor; clk1 base time signal (typically = base clock) of the computer system (µC); clk2 base time signal (typically = base clock) of the control unit (ST); clk3 base time signal (typically = base clock) of the H-bridge (H), preferably of the charge pumps in the H-bridge; CL condenser optics or condenser lens; BL1 left direction indicator; BL2 right direction indicator; BLL1 left signal lamp; BLL2 right signal lamp; Δt delay time; d measured distance; d1 first distance measured; d2 second distance measured; d3 third distance measured; DB data bus (e.g., CAN bus or LIN bus, etc.); DLP micromirror array forStructured deflection of the light beam. F1 first optical filter; F2 second optical filter; F3 third optical filter; FAS1 headlight for low beam left; FAS2 headlight for low beam right; FB road surface; FLP color angle light pulse; FLPF color angle light pulse sequence; FSF1 headlight for high beam left; FSF2 headlight for high beam right; FST1 headlight for daytime running light left; FST2 headlight for daytime running light right; G1 first control terminal of the first transistor (T1) of the first H-bridge (H); G1' first control terminal of the first transistor (T1') of the second H-bridge (H'); G1'' first control terminal of the first transistor (T1'') of the third H-bridge (H''); G2 second control terminal of the second transistor (T2) of the first H-bridge (H); G2' second control terminal of the second transistor (T2') of the second H-bridge (H'); G2'' second control terminal of the second transistor (T2'') of the third H-bridge (H''); G3 thirdControl terminal of the third transistor (T3) of the first H-bridge (H); G3' third control terminal of the third transistor (T3') of the second H-bridge (H'); G3'' third control terminal of the third transistor (T3'') of the third H-bridge (H''); G4 fourth control terminal of the fourth transistor (T4) of the first H-bridge (H); G4' fourth control terminal of the fourth transistor (T4') of the second H-bridge (H'); G4'' fourth control terminal of the fourth transistor (T4'') of the third H-bridge (H''); G5 fifth control terminal of the fifth transistor (T5) of the first H-bridge (H); G6 sixth control terminal of the sixth transistor (T6) of the first H-bridge (H); G7 seventh control terminal of the seventh transistor (T7) of the first H-bridge (H); G8 eighth control terminal of the eighth transistor (T8) of the first H-bridge (H); G9 ninth control terminal of the ninth transistor (T9) of the first H-bridge (H); G10 tenth control terminal of the tenth transistor (T10) of the first H-bridge (H); G11 eleventhControl terminal of the eleventh transistor (T11) of the first H-bridge (H); G12 twelfth control terminal of the twelfth transistor (T12) of the first H-bridge (H); GBP pulsed operation of the H-bridge (H); GND total negative supply voltage or ground. Typically, this is also the reference potential; GND1 first negative supply voltage, for example, in the first H-bridge (H); GND1' first negative supply voltage, for example, in the second H-bridge (H'); GND1'' first negative supply voltage, for example, in the third H-bridge (H''); GND2 second negative supply voltage, for example, in the first H-bridge (H); GND2' second negative supply voltage, for example, in the second H-bridge (H'); GND2'' second negative supply voltage, for example, in the third H-bridge (H''); GWB blocked wavelength range; The first H-bridge corresponds in its basic construction to one of the figures 1 to 8, 12, 13, 16 to 21 and 23. The H-bridge comprises in thisThis does not include the first pulsed LED (LED1, LED1a). For the purposes of this disclosure, it does not include the control unit (ST) and the voltage regulators (SR1, SR2). It therefore has terminals 6 and 7 for the anode terminal A of the LED in question, here the first LED (LED1), and terminals 2 and 3 for the cathode terminal K of the LED in question, here the first LED (LED1), and the terminals for the control electrodes (G1, G2, G3, G4) of the four transistors (T1, T2, T3, T4) of the H-bridge, as well as, in the simplest case, a ground terminal (GND) and a supply voltage terminal (VCC). The first H-bridge preferably consists of a first half-bridge (HB1: T1, T2) and a second half-bridge (T3, T4). In the extreme case, the first half-bridge (HB1: T1, T2) is supplied with electrical energy by a first positive supply voltage (VCC1) and a first negative supply voltage (GND1). In extreme cases, the second half-bridge (HB2: T2, T4) is replaced by a secondThe device is supplied with electrical energy by a positive supply voltage (VCC2) and a second negative supply voltage (GND2). Furthermore, the energy reserves (C_LPPB, C_LPPA, C_LPMA, C_LPMB) of the optional charge pumps (LPPB, LPPA, LPMA, LPMB) can be connected to the charge pumps that are part of the H-bridge as defined in this disclosure. Voltage converters (SVPB, SVPA, SVMA, SVMB) can also be used instead of the charge pumps (LPPB'', LPPA'', LPMA'', LPMB''), if required; H' second H-bridge corresponds in its basic construction to one of Figs. 1, 2, 3, 4, 5, 6, 7 to 8. The second H-bridge, in this sense, does not include the second pulsed LED (LED1b). For the purposes of this disclosure, it does not include the control unit (ST) and the voltage regulators (SR1, SR2). It therefore has terminals 6' and 7' for the anode terminal A' of the second pulsed LED (LED1b), and terminals 2' and 3' for theThe cathode terminal K' of the second pulsed LED (LED1b), and the terminals for the control electrodes (G1', G2', G3', G4') of the four transistors (T1', T2', T3', T4') of the second H-bridge, as well as, in the simplest case, a ground terminal (GND) and a supply voltage terminal (VCC). The second H-bridge preferably consists of a first half-bridge (HB1: T1, T2) and a second half-bridge (HB2: T3, T4). In the extreme case, the first half-bridge (HB1: T1, T2) is supplied with electrical energy by a first positive supply voltage (VCC1) and a first negative supply voltage (GND1). In the extreme case, the second half-bridge (HB2: T2, T4) is supplied with electrical energy by a second positive supply voltage (VCC2) and a second negative supply voltage (GND2). Furthermore, the typically H-bridge specific energy reserves (C_LPPB', C_LPPA', C_LPMA', C_LPMB') of the also typically H-bridge specific optional charge pumps can be used.The second H-bridge (LPPB', LPPA', LPMA', LPMB') may be connected to the charge pumps (LPPB', LPPA', LPMA', LPMB') of the second H-bridge, which may be part of the second H-bridge as defined in this disclosure. Voltage converters (SVPB'', SVPA'', SVMA'', SVMB'') may also be used instead of the charge pumps (LPPB'', LPPA'', LPMA'', LPMB''), if required. The second H-bridge generally corresponds in its structure to the first H-bridge (H); the third H-bridge corresponds in its basic construction to one of Figs. 1, 2, 3, 4, 5, 6, 7 to 8. In this sense, the third H-bridge does not include the third pulsed LED (LED1c). For the purposes of this disclosure, it does not include the control unit (ST) and the voltage regulators (SR1, SR2). It therefore has terminals 6'' and 7'' for the anode terminal A'' of the third pulsed LED (LED1c), and terminals 2'' and 3'' for the cathode terminal K'' of the third pulsed LED (LED1c), and theThe third H-bridge has connections for the control electrodes (G1'', G2'', G3'', G4'') of the four transistors (T1'', T2'', T3'', T4''), as well as, in the simplest case, a ground connection (GND) and a supply voltage connection (VCC). The third H-bridge preferably consists of a first half-bridge (HB1: T1, T2) and a second half-bridge (HB2: T3, T4). In the most extreme case, the first half-bridge (HB1: T1, T2) is supplied with electrical energy by a first positive supply voltage (VCC1) and a first negative supply voltage (GND1). In the most extreme case, the second half-bridge (HB2: T2, T4) is supplied with electrical energy by a second positive supply voltage (VCC2) and a second negative supply voltage (GND2). Furthermore, the typically H-bridge specific energy reserves (C_LPPB'', C_LPPA'', C_LPMA'', C_LPMB'') of the also typically H-bridge specific optional charge pumps (LPPB'', LPPA'', LPMA'', LPMB'') of the secondThe H-bridge is connected to the charge pumps (LPPB'', LPPA'', LPMA'', LPMB'') of the third H-bridge, which are part of the third H-bridge as defined in this disclosure. Voltage converters (SVPB'', SVPA'', SVMA'', SVMB'') may be used instead of the charge pumps (LPPB'', LPPA'', LPMA'', LPMB''), if required. The third H-bridge generally corresponds in its structure to the first H-bridge (H); HB1 is the first half-bridge of the H-bridge comprising the series connection of the first transistor (T1) and the second transistor (T2); HB2 is the second half-bridge of the H-bridge comprising the series connection of the third transistor (T3) and the fourth transistor (T4); HC1 is the first H-bridge control unit; HC2 is the second H-bridge control unit. HCV H-bridge control instrument for measuring the voltage drop across the load in the H-bridge, typically across the first LED (LED1); HCI1 H-bridge control instrument for measuring the current through the first switching element of the H-bridge.so typically through the first transistor (T1), here by measuring the voltage drop across the first transistor (T1); HCI2 H-bridge control instrument for measuring the current through the second switching element of the H-bridge, so typically through the second transistor (T2), here by measuring the voltage drop across the second transistor (T2); HCI3 H-bridge control instrument for measuring the current through the third switching element of the H-bridge, so typically through the third transistor (T3), here by measuring the voltage drop across the third transistor (T3); HCI4 H-bridge control instrument for measuring the current through the fourth switching element of the H-bridge, so typically through the fourth transistor (T4), here by measuring the voltage drop across the fourth transistor (T4); IB internal bus of the headlight (SW); ILED electric current through the first LED (LED1). K cathode of the first LED (LED1); k optional short-circuit statewhere the first LED (LED1) is short-circuited via a supply voltage; Ka Cathode of the first pulsed LED (LED1a); Kb Cathode of the second pulsed LED (LED1b); Kc Cathode of the third pulsed LED (LED1c); Kfz Motor vehicle; Kfz1 First motor vehicle; Kfz2 Second motor vehicle; L_SVMA Energy reserve for the negative voltage transformer (SVMA) to generate a fast turn-on edge, typically an inductor. This energy reserve is typically used together with a freewheeling diode when a negative voltage transformer (SVMA) is used to generate a fast turn-on edge instead of a negative charge pump (LPMA). This energy reserve is not shown in any of the drawings but is part of the disclosure.; L_SVMB Energy reserve for the negative voltage transformer (SVMB) to quickly extract the stored charge carriers, typically an inductor. ThisEnergy reserve is typically used together with a freewheeling diode when a negative voltage converter (SVMB) is used for the rapid removal of stored charge carriers instead of a negative charge pump (LPMB). This energy reserve is not shown in any of the drawings but is part of the disclosure; L_SVPA Energy reserve for the positive voltage converter (SVPA) to generate a fast turn-on edge, typically an inductor. This energy reserve is typically used together with a freewheeling diode when a positive voltage converter (SVPA) is used for the rapid turn-on edge instead of a positive charge pump (LPPA). This energy reserve is not shown in any of the drawings but is part of the disclosure; L_SVPB Energy reserve for the positive voltage converter (SVPB) to rapidly remove thestored charge carriers, typically an inductor. This energy reserve is typically used together with a freewheeling diode when a positive voltage converter (SVPB) is used for the rapid removal of the stored charge carriers instead of a positive charge pump (LPPB). This energy reserve is not shown in any of the drawings but is part of the disclosure; LCD: structured aperture, preferably an LCD-driven aperture or a transparent LCD display for light transmission; LCD_CS: control signal, preferably from the computer system (µC), for controlling the structured aperture, e.g., that of a transparent LCD screen (LCD diascope); LED1: first LED; LED1a: first pulsed LED; LED1b: second pulsed LED; LED2..n: further non-pulsed LEDs or light sources; LPMA: negative charge pump for generating a fast turn-on edge in the first H-bridge (H); LPMA'Negative charge pump for generating a fast turn-on edge in the second H-bridge (H'); LPMA'' negative charge pump for generating a fast turn-on edge in the third H-bridge (H''); LPMB negative charge pump for fast removal of the stored charge carriers in the first H-bridge (H); LPMB' negative charge pump for fast removal of the stored charge carriers in the second H-bridge (H'); LPMB'' negative charge pump for fast removal of the stored charge carriers in the third H-bridge (H''); LPPA positive charge pump for generating a fast turn-on edge in the first H-bridge (H); LPPA' positive charge pump for generating a fast turn-on edge in the second H-bridge (H'); LPPA'' positive charge pump for generating a fast turn-on edge in the third H-bridge (H''); LPPB positive charge pump for fast removal of the stored charge carriers in the first H-bridge (H); LPPB' positive charge pump for rapidExtraction of stored charge carriers in the second H-bridge (H'); LPPB'' positive charge pump for rapid extraction of stored charge carriers in the third H-bridge (H''); LP light pulse; LPF light pulse train; LPWB light pulse-capable wavelength range; µC computer system; MD light-sensitive measuring diode; MS1 first measurement signal; MS2 second measurement signal; MS2 third measurement signal; MV measuring device; NGWB unblocked wavelength range. The unblocked wavelength range comprises the emitted wavelength range (AWB) excluding the blocked wavelength range (GWB); NL1 left fog light; NL2 right fog light; NRL1 left rear fog light; NRL2 right rear fog light; OP optics or optical system; OP2 further optics or further optical system; OP3 further optics or further optical system; PAn on state in pulsed operation (GPB); PAus Off state in pulsed operation (GPB) in which the LED emits no light and in which the charge carriers from the LED are activeremoved; PD1 first photodiode; PD2 second photodiode; PL projection optics or projection lens; PQZ intermediate state in pulsed operation (GPB) in which, due to the short duration of the stay in this intermediate state, a cross-current in the H-bridge is controlled and allowed in the subsequent "PAus" state for faster removal of charge carriers by ensuring that the dwell time Δt in this state is shorter than the time from the beginning of the intermediate state to the switch-off time of those transistors that were conducting in the "PAn" state. The switch-off time of those transistors that were conducting in the "PAn" state can be selected appropriately. Δt can be chosen to be negative or allowed to be negative if the current is limited by the H-bridge. PZ intermediate state of pulsed operation; QDB quasi-continuous operation of the H-bridge. This is the operating mode in which the first LED (LED1) is typically used as the light source of a lighting device. RFReflector, preferably a mirror optic; RF2 further reflector, preferably a further mirror optic; RFL1 left reversing light; RFL2 right reversing light; RL1 left rear light; RL2 right rear light; Rs1 first shunt resistor; Rs2 second shunt resistor; SCHW threshold; SL stray light; SL1 stray light of the first pulsed LED (LED1a); SL2 stray light of the second pulsed LED (LED1b); SR1 first voltage regulator, which generates the first positive supply voltage (VCC1) and the first negative supply voltage (GND1) from the positive total supply voltage (VCC) and the negative total supply voltage (GND); SR2 second voltage regulator, which generates the second positive supply voltage (VCC2) and the second negative supply voltage (GND2) from the positive total supply voltage (VCC) and the negative total supply voltage (GND); SR3 is the third voltage regulator, consisting of the positive total supply voltage (VCC) and theThe third positive supply voltage (VCC3) and the third negative supply voltage (GND3) are generated from the negative total supply voltage (GND); SR4 is the fourth voltage regulator, which generates the fourth positive supply voltage (VCC4) and the fourth negative supply voltage (GND4) from the positive total supply voltage (VCC) and the negative total supply voltage (GND); SR5 is the fifth voltage regulator, which generates the fifth positive supply voltage (VCC5) and the fifth negative supply voltage (GND5) from the positive total supply voltage (VCC) and the negative total supply voltage (GND); SR6 is the sixth voltage regulator, which generates the sixth positive supply voltage (VCC6) and the sixth negative supply voltage (GND4) from the positive total supply voltage (VCC) and the negative total supply voltage (GND); ST is the control device; SVMA is the negative voltage converter for generating a fast turn-on edge in the first H-bridge (H).The negative voltage converter for generating a fast turn-on edge in the first H-bridge (H) can be provided as a substitute for the negative charge pump (LPMA) for generating a fast turn-on edge in the first H-bridge (H), particularly as shown in the figures. The negative voltage converter for generating a fast turn-on edge in the first H-bridge (H) preferably, but not necessarily, generates an output voltage (GND1) relative to a reference potential (GND) that is lower than the most negative of its supply voltages relative to this reference potential (GND); SVMA' negative voltage converter for generating a fast turn-on edge in the second H-bridge (H'). The negative voltage converter for generating a fast turn-on edge in the second H-bridge (H') can be provided as a substitute for the negative charge pump (LPMA') for generating a fast turn-on edge in the second H-bridge (H'), particularly as shown in the figures.The negative voltage converter for generating a fast turn-on edge in the second H-bridge (H') preferably, but not necessarily, produces an output voltage (GND1') relative to a reference potential (GND) that is lower than the most negative of its supply voltages relative to that reference potential (GND); SVMA'' negative voltage converter for generating a fast turn-on edge in the third H-bridge (H''). The negative voltage converter for generating a fast turn-on edge in the third H-bridge (H'') can be provided as a substitute for the negative charge pump (LPMA'') for generating a fast turn-on edge in the third H-bridge (H''), particularly as shown in the figures. The negative voltage converter for generating a fast turn-on edge in the third H-bridge (H'') preferably, but not necessarily, produces an output voltage (GND1'') relative to a reference potential (GND) that is lower than the most negative of itsSupply voltages relative to this reference potential (GND); SVMB negative voltage converter for the rapid extraction of stored charge carriers in the first H-bridge (H). The negative voltage converter for the rapid extraction of stored charge carriers in the first H-bridge (H) can be provided as a substitute for the negative charge pump (LPMB) for the rapid extraction of stored charge carriers in the first H-bridge (H), particularly as shown in the figures. The negative voltage converter for the rapid extraction of stored charge carriers in the first H-bridge (H) preferably, but not necessarily, generates an output voltage (GND2) relative to a reference potential (GND) that is lower than the most negative of its supply voltages relative to this reference potential (GND); SVMB' negative voltage converter for the rapid extraction of stored charge carriers in the second H-bridge (H'). The negative voltage converter for the rapid extraction of theThe negative charge pump (LPMB') for the rapid removal of stored charge carriers in the second H-bridge (H') can be used as a substitute for the negative charge pump (LPMB') for the rapid removal of stored charge carriers in the second H-bridge (H'), particularly as shown in the figures. The negative voltage converter for the rapid removal of stored charge carriers in the second H-bridge (H') preferably, but not necessarily, generates an output voltage (GND2') relative to a reference potential (GND) that is lower than the most negative of its supply voltages relative to this reference potential (GND); SVMB'' negative voltage converter for the rapid removal of stored charge carriers in the third H-bridge (H''). The negative voltage converter for the rapid removal of stored charge carriers in the third H-bridge (H'') can be used as a substitute for the negative charge pump (LPMB'') for the rapid removal of stored charge carriers in the third H-bridge (H''), particularly as shown in the figures.The negative voltage converter for rapidly extracting the stored charge carriers in the second H-bridge (H'') preferably, but not necessarily, generates an output voltage (GND2'') relative to a reference potential (GND) that is lower than the most negative of its supply voltages relative to that reference potential (GND); SVPA is a positive voltage converter for generating a fast turn-on edge in the first H-bridge (H). The positive voltage converter for generating a fast turn-on edge in the first H-bridge (H) can be provided as a substitute for the positive charge pump (LPPA) for generating a fast turn-on edge in the first H-bridge (H), particularly as shown in the figures. The positive voltage converter for generating a fast turn-on edge in the first H-bridge (H) preferably, but not necessarily, generates an output voltage (VCC2) relative to a reference potential (GND) that is higher than the most positiveits supply voltages relative to this reference potential (GND); SVPA' positive voltage converter for generating a fast turn-on edge in the second H-bridge (H'). The positive voltage converter for generating a fast turn-on edge in the second H-bridge (H') can be provided as a substitute for the positive charge pump (LPPA') for generating a fast turn-on edge in the second H-bridge (H'), particularly in the figures. The positive voltage converter for generating a fast turn-on edge in the second H-bridge (H') preferably, but not necessarily, generates an output voltage (VCC2') relative to a reference potential (GND) that is higher than the most positive of its supply voltages relative to this reference potential (GND); SVPA'' positive voltage converter for generating a fast turn-on edge in the third H-bridge (H''). The positive voltage converter for generating a fast turn-on edge in the third H-bridge(H'') can be provided as a substitute for the positive charge pump (LPPA'') for generating a fast turn-on edge in the third H-bridge (H''), particularly as shown in the figures. The positive voltage converter for generating a fast turn-on edge in the third H-bridge (H'') preferably, but not necessarily, generates an output voltage (VCC2'') relative to a reference potential (GND) that is higher than the most positive of its supply voltages relative to this reference potential (GND); SVPB positive voltage converter for fast extraction of the stored charge carriers in the first H-bridge (H). The positive voltage converter for fast extraction of the stored charge carriers in the first H-bridge (H) can be provided as a substitute for the positive charge pump (LPPB) for fast extraction of the stored charge carriers in the first H-bridge (H), particularly as shown in the figures. The positive voltage converter for fast extraction of theThe positive voltage converter (SVPB') for the rapid removal of stored charge carriers from the second H-bridge (H') preferably, but not necessarily, generates an output voltage (VCC1') relative to a reference potential (GND) that is higher than the most positive of its supply voltages relative to this reference potential (GND). The positive voltage converter for the rapid removal of stored charge carriers from the second H-bridge (H') can be provided as a substitute for the positive charge pump (LPPB') for the rapid removal of stored charge carriers from the second H-bridge (H'), particularly as shown in the figures. The positive voltage converter for the rapid removal of stored charge carriers from the second H-bridge (H') preferably, but not necessarily, generates an output voltage (VCC1') relative to a reference potential (GND) that is higher than the most positive of its supply voltages relative to this reference potential (GND).this reference potential (GND); SVPB'' positive voltage converter for the rapid extraction of the stored charge carriers in the third H-bridge (H''). The positive voltage converter for the rapid extraction of the stored charge carriers in the third H-bridge (H'') can be provided as a substitute for the positive charge pump (LPPB'') for the rapid extraction of the stored charge carriers in the third H-bridge (H''), particularly in the figures. The positive voltage converter for the rapid extraction of the stored charge carriers in the third H-bridge (H'') preferably, but not necessarily, generates an output voltage (VCC1'') relative to a reference potential (GND) that is higher than the most positive of its supply voltages relative to this reference potential (GND); SW headlight; SW1 first headlight; SW2 second headlight; SW3 third headlight; SWL headlight light, which is typically non-pulsed; sync synchronization signals with which theThe control device transmits the signal to the measuring device (MV) so that the latter can compare the signal with the signal received by the measuring diode (MD), for example, by calculating a correlation integral between the signal and the signal received by the measuring diode (MD). τ is the lifetime of the charge carriers of the first LED (LED1); τpn is the clearance time. For the purposes of this disclosure, the clearance time is the time that a clearance voltage (URM), which is higher in magnitude than the supply voltage, is applied to the first LED (LED1) in the reverse direction. According to this disclosure, the clearance time is preferably dimensioned such that a residual charge remains in the first LED (LED1) to avoid reducing its lifetime more than necessary. Therefore, the clearance time is preferably shorter than the charge carrier storage time for this higher reverse-biased clearance voltage of the first LED.(LED1). The clearing time (τpn) is preferably less than 95% of the storage time (τsp1), better less than 95% of the storage time (τsp1), better less than 90% of the storage time (τsp1), better less than 85% of the storage time (τsp1), better less than 80% of the storage time (τsp1), better less than 75% of the storage time (τsp1). It is recommended to accurately measure and qualify the effect on the depletion region and the lifetime of the first LED (LED1) and to adjust the clearing time (τpn) and the clearing voltage (URM) appropriately according to the results. This data is generally not available in the LED datasheets. τpp On-time. For the purposes of this disclosure, the on-time is the time that a forward voltage, increased in magnitude compared to the magnitude of the supply voltage, is applied to the first LED (LED1). The turn-on time will be determined according to this disclosure.Preferably dimensioned such that the luminous energy output reaches a predetermined maximum value. The clearing time is therefore preferably shorter than the storage time of the charge carriers for this increased reverse-biased clearing voltage of the first LED (LED1). The turn-on time is preferably less than 95% of the storage time (τsp1), preferably less than 95% of the storage time (τsp1), preferably less than 90% of the storage time (τsp1), preferably less than 85% of the storage time (τsp1), preferably less than 80% of the storage time (τsp1), preferably less than 75% of the storage time (τsp1). This prevents the first LED from being completely flooded with charge carriers. Instead, a charge cloud is formed that penetrates into the region of the other doping within the pn junction. It is recommended to accurately measure and qualify the effect on the junction and lifetime of the first LED (LED1) and to determine the turn-on time (τpp) and the forward voltage.(UDR) suitable to be adjusted according to the results. This data is generally not available in the LED datasheets. τSP0: Charge carrier storage time in the first LED (LED1) when operating with the supply voltage and using the supply voltage as the reverse-biasing clearance voltage of the first LED (LED1). τSP1: Charge carrier storage time in the first LED (LED1) when operating with a voltage higher than the supply voltage in pulsed forward-biased operation of the first LED (LED1) and using a reverse-biasing clearance voltage that is higher in magnitude than the supply voltage. t: time; t0: first time point; t1: second time point; T1: first transistor or first controllable switch that can be controlled by its first control terminal (G1); T1': first transistor of the second H-bridge (H') or first controllable switch of the second H-bridge (H').which is controllable via its first control terminal (G1'); T1" first transistor of the third H-bridge (H'') or first controllable switch of the third H-bridge (H''), which is controllable via its first control terminal (G1"); T2 second transistor or second controllable switch, which is controllable via its second control terminal (G2); T2' second transistor of the second H-bridge (H') or second controllable switch of the second H-bridge (H'), which is controllable via its second control terminal (G2'); T2'' second transistor of the third H-bridge (H'') or second controllable switch of the third H-bridge (H''), which is controllable via its second control terminal (G2''); T3 third transistor or third controllable switch, which is controllable via its third control terminal (G3); T3' third transistor of the second H-bridge (H') or third controllable switch of the second H-bridge (H'), which is controllable via its third control terminal (G3'); T3'' thirdTransistor of the third H-bridge (H'') or third controllable switch of the third H-bridge (H''), controllable by its third control terminal (G3''); T4 fourth transistor or fourth controllable switch, controllable by its fourth control terminal (G4); T4' fourth transistor of the second H-bridge (H') or fourth controllable switch of the second H-bridge (H'), controllable by its fourth control terminal (G4'); T4' fourth transistor of the third H-bridge (H'') or fourth controllable switch of the third H-bridge (H''), controllable by its fourth control terminal (G4''); T5 fifth transistor or fifth controllable switch, controllable by its fifth control terminal (G5); T6 sixth transistor or sixth controllable switch, controllable by its sixth control terminal (G6); T7 seventh transistor or seventh controllable switch, which is controllable via its seventh control terminal (G7); T8 eighthT9: eighth transistor or controllable switch, controllable via its eighth control terminal (G8); T9: ninth transistor or controllable switch, controllable via its ninth control terminal (G9); T10: tenth transistor or controllable switch, controllable via its tenth control terminal (G10); T11: eleventh transistor or controllable switch, controllable via its eleventh control terminal (G11); T12: twelfth transistor or controllable switch, controllable via its twelfth control terminal (G12); TB: time base. The time base generates the device's base time signals. This preferably involves the base time signal (clk1) (typically = base clock) of the computer system (µC), the base time signal (clk2) (typically = base clock) of the control unit (ST), and the base time signal (clk3) (typically = base clock) of the H-bridge (H), preferably of the charge pumps in the H-bridge (H).Basic time signals (clk1, clk2, clk3) can be dependent on each other or the same; TPZmin minimum dwell time in the "PZ" state; TOFIMG two-dimensional arrangement of time-controlled light-sensitive sensors. TWL1 warning light left for vehicles in the left blind spot; TWL2 warning light right for vehicles in the right blind spot; UDR forward voltage at the first LED (LED1), which causes the first LED (LED1) to be flooded with charge carriers. Preferably, the magnitude of the forward voltage in pulsed operation is higher than the voltage used to drive the first LED (LED1) in illumination operation. The on-time (τpp), for which this forward voltage is applied to the first LED (LED1), is therefore dimensioned such that it preferably only represents a fraction of the storage time (τsp1) for a reverse voltage of the same magnitude as this forward voltage. URM reverse voltage or blocking voltage atThe first LED (LED1) is subjected to a reverse voltage that accelerates the removal of charge carriers remaining within the LED1. Preferably, the magnitude of the reverse voltage in pulsed operation is higher than the voltage used to drive the first LED1 during illumination. The clearing time (τpn) during which this reverse voltage is applied to the first LED (LED1) is therefore preferably only a fraction of the storage time (τsp1). The clearing time (τpn) is preferably less than 95% of the storage time (τsp1), preferably less than 95% of the storage time (τsp1), preferably less than 90% of the storage time (τsp1), preferably less than 85% of the storage time (τsp1), preferably less than 80% of the storage time (τsp1), and preferably less than 75% of the storage time (τsp1). It is recommended to accurately measure the effect on the junction and lifetime of the first LED (LED1).and to qualify and adjust the clearing time (τpn) and clearing voltage appropriately according to the results. VCC positive total supply voltage; VCC' positive supply voltage, which switches in magnitude between a voltage value corresponding to a first supply voltage (VCC1) and a second voltage value corresponding to a third supply voltage (VCC3) between quasi-continuous operation (QDB) and pulsed operation (GPB); VCC1 first positive supply voltage, for example in the first H-bridge (H); VCC1' first positive supply voltage, for example in the second H-bridge (H'); VCC1" first positive supply voltage, for example in the third H-bridge (H''); VCC2 second positive supply voltage, for example in the first H-bridge (H); VCC2' second positive supply voltage, for example in the second H-bridge (H'); VCC2" second positive supply voltage, for example in the third H-bridge (H''); VCC3 thirdpositive supply voltage; VLED1 lamp voltage across the first LED (LED1) in the H-bridge (H); VWB wavelength range used for measurement (typically corresponds to the first wavelength range (WB1) emitted by the first LED (LED1)); WB1 first wavelength range; WB2 second wavelength range; WB3 third wavelength range; Z intermediate state in which all four transistors (T1, T2, T3, T4) and possibly other transistors (e.g., T12) are switched off; ZL1 decorative light left; ZL2 decorative light right; List of cited works CN 102 612 231 A ,DE 197 04 496 A1 ,DE 10 2006 041 013 A1 ,DE 10 2006 044 794 A1 ,DE 10 2008 018 718 B4 ,DE 10 2008 2018 B4 ,DE 10 2013 001 273 A1 ,DE 10 2013 001 274 A1 ,DE 10 2013 002 668 A1 ,DE 20 2013 008 067 U1 ,DE 10 2014 108 2015 A1 2014 110 233 A1 ,DE 10 2016 116 718 A1DE 10 2016 205 563 A1 ,DE 10 2016 202 505 A1 ,DE 20 2017 103 902 U1 ,EP 07 4 70 EP 2016 2016 B1 ,EP 2 761 978 B1 ,EP 0 762 651 A2 ,EP 2 783 232 B1 ,JP 2005 - 158 483 A ,US 4 571 506 A ,US 9 653 642 B1 ,US 2016 302 A 307 ,WO 2014 / 124 768 A1 , Cited Non-Patent Literature WESEN, Bjorn [et al.]: “Fastest way of doing on / off-modulation of an LED?”. June 22, 2011, edited June 23, 2014. 4th p. URL: https: / / electronics.stackexchange.com / questions / 15818 / fastest-way-of-doingon-off-modulation-of-a-led [accessed January 23, 2018] “TPS28226 High-Frequency 4-A Sink Synchronous MOSFET Drivers”, application note from Texas Instruments “2A Synchronous Buck Power MOSFET Driver”, an application note from Microchip for the Microchip product MCP14628

Claims

Device for controlling at least one light-emitting diode (LED1) to generate short light pulses (LP),- with an H-bridge (H) consisting of a first half-bridge (HB1: T1, T2) with a first transistor (T1) and a second transistor (T2) and a second half-bridge (HB2: T2, T3) with a third transistor (T3) and a fourth transistor (T4),- wherein the H-bridge (H) is controlled by a control unit (ST) and- wherein the H-bridge (H) can be operated by the control unit (ST) in pulsed mode (GPB) and in quasi-continuous mode (QDB) and- wherein the first half-bridge (HB1: T1, T2) is supplied with electrical energy from a first positive supply voltage (VCC1) and a first negative supply voltage (GND1) and- wherein the second half-bridge (HB2: T3,T4) is supplied with electrical energy from a second positive supply voltage (VCC2) and a second negative supply voltage (GND2) and- wherein the light-emitting diode (LED1) is connected with its cathode (K) to the output of the first half-bridge (HB1: T1, T2) and- wherein the light-emitting diode (LED1) is connected with its anode (A) to the output of the second half-bridge (HB2: T3, T4) and- wherein the first positive supply voltage (VCC1) and the second positive supply voltage (VCC2) can be equal and- wherein the first negative supply voltage (GND1) and the second negative supply voltage (GND2) can be equal and- wherein the light source, in particular the one or more light-emitting diodes (LED1), represents the load of the H-bridge (H) between the output of the first half-bridge (HB1: T1, T2) and the output of the second half-bridge (HB2: T3, T4) and- wherein the control device (ST) is designed to operate in pulsed mode (GPB) a “PAn” condition,in which a forward voltage in the forward direction of the light-emitting diode (LED1) is applied to the light-emitting diode (LED1) through the H-bridge (H), is not maintained by the H-bridge (H) for longer than a turn-on time (τpp), and- wherein the control device (ST) is designed so that in pulsed operation (GPB) a "PAus" state, in which a reverse voltage against the forward direction of the light-emitting diode (LED1) is applied to the light-emitting diode (LED1) through the H-bridge (H), is not maintained by the H-bridge (H) for longer than a turn-off time (τpn), and- wherein the turn-off time (τpn) is less than the charge carrier lifetime (τ) in the PN junction of the light-emitting diode (LED1), and- wherein the turn-on time (τpp) is less than the charge carrier lifetime (τ) in the PN junction of the light-emitting diode (LED1). Device according to claim 1, wherein the device is supplied with a positive base supply voltage (VCC) and a negative base supply voltage (GND), and comprising at least one voltage converter (SVPA, SVPB, SVMA, SVMB) or at least one charge pump (LPPA, LPPB, LPMA, LPMB) for generating the first positive supply voltage (VCC1), or for generating the second positive supply voltage (VCC2), or for generating the first negative supply voltage (GND1), or for generating the second negative supply voltage (GND2), or for generating a third supply voltage (VCC3) for temporarily supplying energy to the light source, wherein the largest voltage difference between the output voltage of the at least one voltage converter or the at least one charge pump (LPPA, LPPB, LPMA,LPMB) to the positive base supply voltage (VCC) or the negative base supply voltage (GND) is greater than the voltage difference between the first positive base supply voltage (VCC) and the negative base supply voltage (GND). Device according to claim 1 or 2- wherein the forward voltage in the “PAn” state of the H-bridge (H), which is applied to the light-emitting diode (LED1) in this state, is greater in magnitude in pulsed operation (GPB) than in quasi-continuous operation (QDB) and / or- wherein the reverse voltage in the “PAus” state of the H-bridge (H), which is applied to the light-emitting diode (LED1) in this state, is greater in magnitude in pulsed operation (GPB) than in quasi-continuous operation (QDB). Device according to one or more of claims 1 to 3, wherein the H-bridge has a further transistor (T12), and wherein the further transistor (T12) can connect a terminal of the light-emitting diode (LED1) to a third positive supply voltage (VCC3), and wherein the supply of the light-emitting diode (LED1) in quasi-continuous operation (QDB) when using the light-emitting diode (LED1) as a light source for lighting purposes is from the third supply voltage (VCC3), and wherein the supply of the light-emitting diode (LED1) in pulsed operation (GPB) is the supply of the first LED (LED1) from the first supply voltage (VCC1). Time-of-flight camera with a light pulse source comprising a device according to one or more of the preceding claims. A method for operating a device according to claim 5, comprising the steps of: - blocking the first transistor (T1) of the first half-bridge (HB1) of the H-bridge (H), such that the first transistor (T1) no longer conducts electrically between the first positive supply voltage (VCC1) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this first transistor (T1) was previously conducting between these terminals of the first transistor (T1); - blocking the fourth transistor (T4) of the second half-bridge (HB2) of the H-bridge (H), such that the fourth transistor (T4) no longer conducts electrically between the second negative supply voltage (GND2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this fourth transistor (T4) was previously conducting between these terminals of the fourth transistor (T4);- Switching off the third transistor (T3) of the second half-bridge (HB2) of the H-bridge (H), so that the third transistor (T3) no longer conducts electrically between the second positive supply voltage (VCC2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this third transistor (T3) was previously conducting between these terminals of the third transistor (T3); - Switching on the second transistor (T2) of the first half-bridge (HB1) of the H-bridge (H), so that the second transistor (T2) conducts electrically between the first negative supply voltage (GND1) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this second transistor (T2) was previously electrically blocking (=high impedance) between these terminals of the second transistor (T2);- Switching on the second transistor (T12) of the H-bridge (H), so that the second transistor (T12) conducts electrically between the third positive supply voltage (VCC3) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this second transistor (T12) was previously electrically blocking (high impedance) between these terminals of the second transistor (T12); - Supplying electrical current from the third positive supply voltage (VCC3) via the second transistor (T12) to the light-emitting diode (LED1); - Discharge of the electrical current from the light-emitting diode (LED1) to the first negative supply voltage (GND1); - Emission of light for illumination purposes by the light-emitting diode (LED1). A method for operating a device according to one or more of claims 5 or 6, comprising the steps of: - blocking the further transistor (T12) of the H-bridge (H), so that the further transistor (T12) no longer conducts electrically between the third positive supply voltage (VCC3) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this further transistor (T12) was previously conducting between these terminals of the further transistor (T12); - blocking the first transistor (T1) of the first half-bridge (HB1) of the H-bridge (H), so that the first transistor (T1) no longer conducts electrically between the first positive supply voltage (VCC1) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this first transistor (T1) was previously conducting between these terminals of the first transistor (T1);- Switching off the fourth transistor (T4) of the second half-bridge (HB2) of the H-bridge (H), so that the fourth transistor (T4) no longer conducts electrically between the second negative supply voltage (GND2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this fourth transistor (T4) was previously conducting between these terminals of the fourth transistor (T4); - Switching on the third transistor (T3) of the second half-bridge (HB2) of the H-bridge (H), so that the third transistor (T3) conducts electrically between the second positive supply voltage (VCC2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this third transistor (T3) was previously electrically blocking (=high impedance) between these terminals of the third transistor (T3);- Switching on the second transistor (T2) of the first half-bridge (HB1) of the H-bridge (H), so that the second transistor (T2) conducts electrically between the first negative supply voltage (GND1) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this second transistor (T2) was previously electrically blocking (high impedance) between these terminals of the second transistor (T2); - Injecting electrical current from the second positive supply voltage (VCC2) via the third transistor (T3) of the second half-bridge (HB2) of the H-bridge (H) into the light-emitting diode (LED1); - Discharge of the electrical current from the light-emitting diode (LED1) via the second transistor (T2) of the first half-bridge (HB1) of the H-bridge (H) into the first negative supply voltage (GND1); - Emitting light for measurement purposes through the light-emitting diode (LED1). Method for operating a device for emitting a light pulse (LP) by means of a device according to one or more of claims 1 to 3 or 5, comprising the steps of: assuming an intermediate state (PZ), in particular from a "PAus" state; a first transverse current with a first maximum transverse current magnitude occurs in the first half-bridge (HB1: T1, T2) of the H-bridge; and a second transverse current with a second maximum transverse current magnitude occurs in the second half-bridge (HB2: T3, T4) of the H-bridge, comprising the sub-steps of: blocking the first transistor (T1) of the first half-bridge (HB1) of the H-bridge (H), such that the first transistor (T1) no longer conducts electrically between the first positive supply voltage (VCC1) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this first transistor (T1) was previously electrically conducting between these terminals of the first transistor (T1);• Blocking the second transistor (T2) of the first half-bridge (HB1) of the H-bridge (H), so that the second transistor (T2) no longer conducts electrically between the first negative supply voltage (GND1) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this second transistor (T2) was previously electrically conductive between these terminals of the second transistor (T2); • Blocking the third transistor (T3) of the second half-bridge (HB2) of the H-bridge (H), so that the third transistor (T3) no longer conducts electrically between the second positive supply voltage (VCC2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this third transistor (T3) was previously electrically conductive between these terminals of the third transistor (T3);• Switching off the fourth transistor (T4) of the second half-bridge (HB2) of the H-bridge (H), so that the fourth transistor (T4) no longer conducts electrically between the second negative supply voltage (GND2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this fourth transistor (T4) was previously electrically conductive between these terminals of the fourth transistor (T4); - Entering a "PAn" state (PAn) by transitioning from the intermediate state (PZ), comprising the sub-steps: • Switching off the first transistor (T1) of the first half-bridge (HB1) of the H-bridge (H), so that the first transistor (T1) no longer conducts electrically between the first positive supply voltage (VCC1) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this first transistor (T1) was previously electrically conductive between these terminals of the first transistor (T1);• Switching on the second transistor (T2) of the first half-bridge (HB1) of the H-bridge (H), so that the second transistor (T2) conducts electrically between the first negative supply voltage (GND1) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this second transistor (T2) was previously electrically blocking (=high impedance) between these terminals of the second transistor (T2); • Switching on the third transistor (T3) of the second half-bridge (HB2) of the H-bridge (H), so that the third transistor (T3) conducts electrically between the second positive supply voltage (VCC2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this third transistor (T3) was previously electrically blocking (=high impedance) between these terminals of the third transistor (T3);• Switching off the fourth transistor (T4) of the second half-bridge (HB2) of the H-bridge (H), so that the fourth transistor (T4) no longer conducts electrically between the second negative supply voltage (GND2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this fourth transistor (T4) was previously electrically conductive between these terminals of the fourth transistor (T4); - Entering a "PQZ" state (PQZ) by transitioning from the "PAn" state, • comprising the sub-steps • Switching on the first transistor (T1) of the first half-bridge (HB1) of the H-bridge (H), so that the first transistor (T1) conducts electrically between the first positive supply voltage (VCC1) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this first transistor (T1) was previously electrically blocking (=high impedance) between these terminals of the first transistor (T1);• Blocking the second transistor (T2) of the first half-bridge (HB1) of the H-bridge (H), so that the second transistor (T2) no longer conducts electrically between the first negative supply voltage (GND1) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this second transistor (T2) was previously electrically conductive between these terminals of the second transistor (T2); • Blocking the third transistor (T3) of the second half-bridge (HB2) of the H-bridge (H), so that the third transistor (T3) no longer conducts electrically between the second positive supply voltage (VCC2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this third transistor (T3) was previously electrically conductive between these terminals of the third transistor (T3);• Switching on the fourth transistor (T4) of the second half-bridge (HB2) of the H-bridge (H), so that the fourth transistor (T4) conducts electrically between the second negative supply voltage (GND2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this fourth transistor (T4) was previously electrically blocking (=high impedance) between these terminals of the fourth transistor (T4); • Exiting the “PQZ” state after a dwell time Δt;- Entering a “PAus” state (PAus) by transitioning from the “PQZ” state, • wherein a third transverse current with a third maximum transverse current magnitude occurs in the first half-bridge (HB1: T1, T2) of the H-bridge and • wherein a fourth transverse current with a fourth maximum transverse current magnitude occurs in the second half-bridge (HB2: T3, T4) of the H-bridge, comprising the sub-steps • turning on the first transistor (T1) of the first half-bridge (HB1) of the H-bridge (H), such that the first transistor (T1) conducts electrically between the first positive supply voltage (VCC1) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this first transistor (T1) was previously conducting between these terminals of the first transistor (T1);• Blocking the second transistor (T2) of the first half-bridge (HB1) of the H-bridge (H), so that the second transistor (T2) no longer conducts electrically between the second negative supply voltage (GND2) and the output of the first half-bridge (HB1) of the H-bridge (H), provided that this second transistor (T2) was previously electrically conductive between these terminals of the second transistor (T2); • Blocking the third transistor (T3) of the second half-bridge (HB2) of the H-bridge (H), so that the third transistor (T3) no longer conducts electrically between the second positive supply voltage (VCC2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this third transistor (T3) was previously electrically conductive between these terminals of the third transistor (T3);• Switching on the fourth transistor (T4) of the second half-bridge (HB2) of the H-bridge (H), such that the fourth transistor (T4) conducts electrically between the second negative supply voltage (GND2) and the output of the second half-bridge (HB2) of the H-bridge (H), provided that this fourth transistor (T4) was previously electrically conducting between these terminals of the fourth transistor (T4). • wherein the third maximum cross-current is greater than the first maximum cross-current and / or • wherein the “PZ” state differs from the “PQZ” state in that all transistors to be switched off (T3, T2) are switched off when leaving the “PZ” state, whereas they may still be electrically conducting temporarily when leaving the “PQZ” state. The method of claim 8 comprises the additional steps of: determining the third transverse current magnitude and / or the fourth transverse current magnitude as a control parameter, wherein the respective maximum transverse current magnitude and / or the time course of the respective transverse current magnitude can be recorded; changing at least one of the following parameters of the method of claim 7 depending on the control parameter: • changing the dwell time Δt in the “PQZ” state; • changing the voltage magnitude of the voltage difference between the second supply voltage (VCC2) and the first negative supply voltage (GND1).

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