Communication method and apparatus

Abstract

Disclosed in embodiments of the present application are a communication method and apparatus. The method comprises: generating a first signal, wherein the first signal comprises a first-channel signal and a second-channel signal, the first-channel signal comprises X first data signals, each first data signal is represented by formula (I), the second-channel signal comprises Y second data signals and M first phase noise tracking reference signals (PTRSs), each second data signal is represented by formula (II), each first PTRS is represented by formula (III), θ1 belongs to [0, 2π), θ2 belongs to [0, 2π), the M first PTRSs in formula (IV) are used for processing phase noise, the first-channel signal and the second-channel signal are continuously interleaved, X, Y, M, and N are all integers greater than or equal to 1, and a, b, and c are all real numbers; and sending the first signal to a terminal device. By means of the embodiments of the present application, the accuracy of phase noise processing can be improved, and the communication performance is improved.

Description

Communication method and device

[0001] This application claims priority to the Chinese patent application with application number 202311684424.X filed with the State Intellectual Property Office of China on December 7, 2023, and priority to the Chinese patent application with the invention name “A Communication Method and Device”, all contents of which are incorporated by reference into this application. Technical Field

[0002] The present application relates to the field of communication technology, and in particular to a communication method and device. Background Art

[0003] To transmit signals over long distances, wireless communication systems require orthogonal frequency division multiplexing (OFDM) power amplification. Due to technical and cost limitations, a power amplifier typically provides linear amplification only within a certain range. Exceeding this range results in signal distortion. This distortion prevents the receiver from correctly interpreting the signal. To ensure that signal peaks remain within the linear range of the power amplifier, the average power must be reduced, which results in lower power amplifier efficiency or, equivalently, a reduced coverage range. To meet coverage requirements, signal generation technologies with a low peak-to-average power ratio (PAPR) are often selected.

[0004] In this technical field, single carrier-offset quadrature amplitude modulation (SC-OQAM) and single carrier transform spread orthogonal frequency division multiplexing (DFT-s-OFDM with FTSS) can reduce the PAPR of discrete Fourier transform spreading orthogonal frequency division multiplexing (DFT-s-OFDM) waveforms, and are alternative waveform technologies for future mobile communications and high-frequency scenarios. However, when the modulation method of the transmitted signal changes from the traditional quadrature amplitude modulation (QAM) constellation point to low-PAPR OQAM or DFT-S-OFDM with FTSS, the phase noise cannot be estimated by separating the real and imaginary parts, affecting communication performance.

[0005] Summary of the Invention

[0006] The embodiments of the present application provide a communication method and apparatus, which can improve the accuracy of phase noise processing and enhance communication performance.

[0007] In a first aspect, an embodiment of the present application provides a communication method, which is applied to a network device, or a chip or circuit configured in the network device, including:

[0008] Generate a first signal, the first signal includes a first signal and a second signal, the first signal includes X first data signals, the first data signal is The second signal path includes Y second data signals and M first phase noise tracking pilot signals PTRS. The second data signal is The first PTRS is The θ1 belongs to [0,2π), the θ2 belongs to [0,2π), The M first PTRSs are used to process phase noise, the first signal and the second signal are continuously interleaved, X, Y, M and N are all integers greater than or equal to 1, and a, b and c are all real numbers; a first signal is sent to the terminal device.

[0009] By continuously interleaving the first signal and the second signal, the phase angle between the first signal and the second signal satisfies A first pilot signal reception (PTRS) is set in the second signal to process phase noise. For example, if the first signal is a real signal, a real pilot signal is set in the second signal's place where the imaginary signal was originally set. This ensures that the interference of the data carried by the first signal on the first PTRS is in the same direction as the first PTRS, maximizing the signal energy of the first PTRS. This utilizes the first PTRS to process phase noise, improving phase noise processing accuracy and enhancing communication performance.

[0010] In one possible design, the positive and negative phases of the first PTRS are determined based on the positive and negative phases of interference caused by data carried by the first signal on the first PTRS. By determining the positive and negative phases of the first PTRS based on the positive and negative phases of interference caused by data carried by the first signal on the first PTRS, the energy of the first PTRS is maximized, thereby utilizing the first PTRS to process phase noise and improve the accuracy of phase noise processing.

[0011] In one possible design, the positive and negative phases of the first PTRS are determined based on the positive and negative phases of interference caused by data carried by the first signal on the first PTRS. By determining the positive and negative phases of the first PTRS based on the positive and negative phases of interference caused by data carried by the first signal on the first PTRS, the signal energy of the transmitted PTRS can be reduced. This reduces the signal energy of the first PTRS while increasing the signal energy of the data without changing the ability of the receiving end to process phase noise, as the total energy is constant.

[0012] In one possible design, the positive and negative phases of the first PTRS are the same as the positive and negative phases of interference caused by data carried by the first signal on the first PTRS. This maximizes the energy of the first PTRS, thereby utilizing the first PTRS to process phase noise and improve the accuracy of phase noise processing.

[0013] In a possible design, the first signal further includes M second PTRSs, one second PTRS corresponds to one first PTRS, and the second PTRS is The M second PTRSs are used to carry data, and d is a real number. Thus, the second PTRSs are used to carry constellation symbols to carry more bits, thereby ensuring data transmission efficiency.

[0014] In one possible design, the positive and negative phases of the second PTRS are the same as those of the first PTRS, so that the positive and negative phases of the interference of the second PTRS on the first PTRS are the same as those of the first PTRS, thereby maximizing the energy of the first PTRS.

[0015] In one possible design, the second PTRS is adjacent to the first PTRS, so as to facilitate adjustment of the positive and negative phases of the second PTRS in the first signal to better match the impact on the first PTRS in the second signal.

[0016] In one possible design, the M first PTRSs are evenly spaced in the second signal, so that the impact of the data carried by the first signal on the multiple first PTRSs is consistent. For example, the interference of the data carried by the first signal on the multiple first PTRSs is ensured to be positive phase.

[0017] In one possible design, a predefined PTRS pattern is sent to the terminal device. The PTRS pattern is used to determine PTRS parameters. The terminal device determines the PTRS parameters corresponding to the PTRS pattern based on a current scheduling bandwidth, determines a mapping position of a first PTRS in the first signal based on the PTRS parameters, obtains the first PTRS at the mapping position in the first signal, and processes phase noise using the first PTRS.

[0018] In a second aspect, an embodiment of the present application provides a communication method, which is applied to a terminal device, or a chip or circuit configured in the terminal device, including:

[0019] Receive a first signal sent by a network device, the first signal including a first signal and a second signal, the first signal including X first data signals, the first data signal being The second signal path includes Y second data signals and M first phase noise tracking pilot signals PTRS. The second data signal is The first PTRS is The θ1 belongs to [0,2π), the θ2 belongs to [0,2π), The M first PTRSs are used to process phase noise, the first signal and the second signal are continuously interleaved, X, Y, M, and N are all integers greater than or equal to 1, and a, b, and c are all real numbers; based on the M first PTRSs, phase noise is processed to improve communication performance.

[0020] By continuously interleaving the first signal and the second signal, the phase angle between the first signal and the second signal satisfies A first pilot signal reception (PTRS) is set in the second signal to process phase noise. For example, if the first signal is a real signal, a real pilot signal is set in the second signal's place where the imaginary signal was originally set. This ensures that the interference of the data carried by the first signal on the first PTRS is in the same direction as the first PTRS, maximizing the signal energy of the first PTRS. Phase noise is processed using the first PTRS, improving the accuracy of phase noise processing.

[0021] In one possible design, the positive and negative phases of the first PTRS are determined based on the positive and negative phases of interference caused by data carried by the first signal on the first PTRS. By determining the positive and negative phases of the first PTRS based on the positive and negative phases of interference caused by data carried by the first signal on the first PTRS, the signal energy of the transmitted PTRS can be reduced, thereby reducing the signal energy of the first PTRS while increasing the signal energy of the data without changing the ability of the receiving end to process phase noise, because the total energy is constant.

[0022] In one possible design, the positive and negative phases of the first PTRS are the same as the positive and negative phases of interference caused by data carried by the first signal on the first PTRS. This maximizes the energy of the first PTRS, thereby utilizing the first PTRS to process phase noise and improve the accuracy of phase noise processing.

[0023] In a possible design, the first signal further includes M second PTRSs, one second PTRS corresponds to one first PTRS, and the second PTRS is The M second PTRSs are used to carry data, and d is a real number. Thus, the second PTRSs are used to carry constellation symbols to carry more bits, thereby ensuring data transmission efficiency.

[0024] In one possible design, the positive and negative phases of the second PTRS are the same as those of the first PTRS, so that the positive and negative phases of the interference of the second PTRS on the first PTRS are the same as those of the first PTRS, thereby maximizing the energy of the first PTRS.

[0025] In one possible design, the second PTRS is adjacent to the first PTRS, so as to facilitate adjustment of the positive and negative phases of the second PTRS in the first signal to better match the impact on the first PTRS in the second signal.

[0026] In one possible design, the M first PTRSs are evenly spaced in the second signal, so that the impact of the data carried by the first signal on the multiple first PTRSs is consistent. For example, the interference of the data carried by the first signal on the multiple first PTRSs is ensured to be positive phase.

[0027] In one possible design, a predefined PTRS pattern sent by the network device is received, where the PTRS pattern is used to determine PTRS parameters. A mapping position of a first PTRS in the first signal is determined based on the PTRS parameters, so that the first PTRS is obtained at the mapping position in the first signal, and phase noise is processed based on the first PTRS.

[0028] In a third aspect, an embodiment of the present application provides a communication device, the device comprising:

[0029] The processing module is configured to generate a first signal, wherein the first signal includes a first signal and a second signal, wherein the first signal includes X first data signals, and the first data signal is The second signal path includes Y second data signals and M first phase noise tracking pilot signals PTRS. The second data signal is The first PTRS is The θ1 belongs to [0,2π), the θ2 belongs to [0,2π), The M first PTRSs are used to process phase noise, the first signal and the second signal are continuously interleaved, X, Y, M, and N are all integers greater than or equal to 1, and a, b, and c are all real numbers;

[0030] A sending module is used to send a first signal to a terminal device.

[0031] In one possible design, the positive and negative phases of the first PTRS are determined according to the positive and negative phases of interference caused by data carried by the first signal on the first PTRS.

[0032] In one possible design, the positive and negative phases of the first PTRS are the same as the positive and negative phases of interference caused by data carried by the first signal on the first PTRS.

[0033] In a possible design, the first signal further includes M second PTRSs, one second PTRS corresponds to one first PTRS, and the second PTRS is The M second PTRSs are used to carry data, and d is a real number.

[0034] In one possible design, the positive and negative phases of the second PTRS are the same as those of the first PTRS.

[0035] In one possible design, the second PTRS is adjacent to the first PTRS.

[0036] In one possible design, the M first PTRSs are arranged at equal intervals in the second signal.

[0037] In one possible design, the sending module is further used to send a predefined PTRS pattern to the terminal device, where the PTRS pattern is used to determine PTRS parameters.

[0038] In a fourth aspect, an embodiment of the present application provides a communication device, the device comprising:

[0039] The receiving module is configured to receive a first signal sent by a network device, wherein the first signal includes a first signal and a second signal, wherein the first signal includes X first data signals. The second signal path includes Y second data signals and M first phase noise tracking pilot signals PTRS. The second data signal is The first PTRS is The θ1 belongs to [0,2π), the θ2 belongs to [0,2π), The M first PTRSs are used to process phase noise, the first signal and the second signal are continuously interleaved, X, Y, M, and N are all integers greater than or equal to 1, and a, b, and c are all real numbers;

[0040] A processing module is configured to process phase noise based on the M first PTRSs.

[0041] In one possible design, the positive and negative phases of the first PTRS are determined according to the positive and negative phases of interference caused by data carried by the first signal on the first PTRS.

[0042] In one possible design, the positive and negative phases of the first PTRS are the same as the positive and negative phases of interference caused by data carried by the first signal on the first PTRS.

[0043] In a possible design, the first signal further includes M second PTRSs, one second PTRS corresponds to one first PTRS, and the second PTRS is The M second PTRSs are used to carry data, and d is a real number.

[0044] In one possible design, the positive and negative phases of the second PTRS are the same as those of the first PTRS.

[0045] In one possible design, the second PTRS is adjacent to the first PTRS.

[0046] In one possible design, the M first PTRSs are arranged at equal intervals in the second signal.

[0047] In one possible design, the receiving module is further used to receive a predefined PTRS pattern sent by the network device, where the PTRS pattern is used to determine PTRS parameters.

[0048] In a fifth aspect, the present application provides a communication device, which includes a processor and a memory, wherein the memory is used to store a computer program; the processor is used to execute the computer program stored in the memory, so that the communication device performs the method as described in any one of the first aspects.

[0049] In a sixth aspect, the present application provides a communication device, comprising a processor and a memory, wherein the memory is used to store a computer program; the processor is used to execute the computer program stored in the memory so that the communication device performs a method as described in any one of the second aspects.

[0050] In a seventh aspect, the present application provides a communication device, which may be a network device, a device in a network device, or a device that can be used in conjunction with a network device. The communication device may also be a chip system. The communication device may execute the method described in the first aspect. The functions of the communication device may be implemented by hardware, or by hardware executing corresponding software implementations. The hardware or software includes one or more modules corresponding to the above functions. The module may be software and / or hardware. The operations and beneficial effects performed by the communication device may refer to the methods and beneficial effects described in the first aspect above, and any repetitions will not be repeated.

[0051] In an eighth aspect, the present application provides a communication device, which may be a terminal device, a device in a terminal device, or a device that can be used in conjunction with a terminal device. The communication device may also be a chip system. The communication device may execute the method described in the second aspect. The functions of the communication device may be implemented by hardware or by hardware executing corresponding software implementations. The hardware or software includes one or more modules corresponding to the above functions. The module may be software and / or hardware. The operations and beneficial effects performed by the communication device may refer to the methods and beneficial effects described in the second aspect above, and any repetitions will not be repeated.

[0052] In a ninth aspect, the present application provides a computer-readable storage medium for storing a computer program. When the computer program is executed, the method described in any one of the first and second aspects is implemented.

[0053] In a tenth aspect, the present application provides a computer program product comprising a computer program, which, when executed, enables the method described in any one of the first and second aspects to be implemented.

[0054] In the eleventh aspect, an embodiment of the present application provides a communication system, which includes at least one terminal device and at least one network device, the network device is used to execute the steps in the above-mentioned first aspect, and the terminal device is used to execute the steps in the above-mentioned second aspect.

[0055] In a twelfth aspect, a chip is provided, which includes a processor and a communication interface, wherein the communication interface is used to communicate with an external device or an internal device, and the processor is used to implement the methods in the above aspects.

[0056] In one possible design, the chip may further include a memory storing a computer program or instructions, and the processor is configured to execute the computer program or instructions stored in the memory, or other programs or instructions. When the computer program or instructions are executed, the processor is configured to implement the aforementioned various aspects of the method.

[0057] In one possible design, the chip can be integrated into a terminal device or a network device. BRIEF DESCRIPTION OF THE DRAWINGS

[0058] FIG1 is a schematic structural diagram of a communication system provided in an embodiment of the present application;

[0059] FIG2 is a schematic diagram of peak power and average power;

[0060] FIG3 is a schematic diagram of an OFDM amplitude;

[0061] FIG4 is a schematic diagram showing the effect of phase noise on a received signal;

[0062] FIG5 is a schematic diagram of a processing flow of a DFT-s-OFDM technology;

[0063] FIG6 is a schematic diagram of SC-OQAM signal processing;

[0064] FIG7 is a schematic diagram of SC-QAM signal processing;

[0065] FIG8 is a schematic diagram of an SC-QAM waveform;

[0066] FIG9 is a schematic diagram of an SC-OQAM waveform;

[0067] FIG10 is a schematic diagram of DFT-S-OFDM with FTSS signal processing;

[0068] FIG11 is a schematic diagram of filtering of a DFT-S-OFDM with FTSS;

[0069] FIG12 is a schematic diagram of a PTRS pattern of DFT-s-OFDM;

[0070] FIG13 is a schematic diagram of waveform interference of a filter;

[0071] FIG14 is a schematic diagram of a performance comparison;

[0072] FIG15 is a flow chart of a communication method provided in an embodiment of the present application;

[0073] FIG16 is a schematic diagram of a first signal;

[0074] FIG17 is a schematic diagram of another first signal;

[0075] FIG18 is a schematic structural diagram of a communication device provided in an embodiment of the present application;

[0076] FIG19 is a schematic structural diagram of another communication device provided in an embodiment of the present application;

[0077] FIG20 is a schematic diagram of the structure of a network device provided in an embodiment of the present application;

[0078] Figure 21 is a structural diagram of a terminal device provided in an embodiment of the present application. DETAILED DESCRIPTION

[0079] As shown in FIG1 , FIG1 is a schematic diagram of the structure of a communication system provided in an embodiment of the present application. The communication system may include network equipment and terminal equipment. Among them:

[0080] A network device is a device deployed in a wireless access network to provide wireless communication functions for terminal devices. Network devices may include various forms of macro base stations, micro base stations (also known as small stations), relay stations, access points, etc. In systems using different wireless access technologies, the names of network devices may be different, such as base transceiver stations (BTS) in global system for mobile communication (GSM) or code division multiple access (CDMA) networks, node B (NB) in wideband code division multiple access (WCDMA), and evolved node B (eNB) in long term evolution (LTE). A network device can also be a wireless controller in a cloud radio access network (CRAN) scenario. A network device can also be a base station device in a fifth generation mobile communication system (5G) network or next generation wireless communication, or a network device in a future evolved public land mobile network (PLMN) network. A network device can also be a wearable device or an in-vehicle device. Network devices can also be transmission and reception points (TRPs).

[0081] Terminal devices may include various handheld devices with wireless communication capabilities, in-vehicle devices, wearable devices, computing devices, or other processing devices connected to a wireless modem. Terminal devices may be mobile stations (MS), subscriber units (subscriber units), cellular phones, smart phones, wireless data cards, personal digital assistants (PDAs), tablet computers, wireless modems, handheld devices (handsets), laptop computers, machine type communication (MTC) terminals, etc.

[0082] The communication system can be applicable to a long term evolution (LTE) system, a universal mobile telecommunications system (UMTS) system, a code division multiple access (CDMA) system, a wireless local area network (WLAN) or a fifth generation mobile communication system (5G) or a next generation wireless communication system, etc.

[0083] Peak to average power ratio (PAPR), also known as peak-to-average power ratio. A wireless signal observed in the time domain is a sinusoidal wave with a constantly changing amplitude. The amplitude is not constant. The peak amplitude of the signal in one cycle is different from the peak amplitude in other cycles. Therefore, the average power and peak power in each cycle are different. Over a long period of time, the peak power is the maximum transient power with a certain probability of occurring. The probability is usually taken as 0.01% (i.e., 10 -4 The ratio of the peak power at this probability to the total average power of the system is the peak-to-average power ratio. Figure 2 shows a diagram of peak power and average power. Figure 2 includes two lines: the first line represents peak power, and the second line represents average power. The ratio of peak power to average power is the peak-to-average power ratio.

[0084] The factors that affect the system peak-to-average ratio include the following: (1) The peak-to-average ratio of the baseband signal, such as the baseband signal modulated by 1024-QAM, which has a large peak-to-average ratio. The baseband signal modulated by quadrature phase shift keying (QPSK) and binary phase shift keying (BPSK) has a peak-to-average ratio of 1. Among them, QPSK and BPSK can be understood as the signal amplitude being constant and only the phase changing. (2) The peak-to-average ratio introduced by the superposition of multi-carrier power, such as the 10*logN of orthogonal frequency division multiplexing (OFDM). As shown in Figure 3, Figure 3 is a schematic diagram of OFDM amplitude. The vertical axis is the OFDM amplitude and the horizontal axis is the subcarrier index. The ratio of peak power to average power of OFDM is large.

[0085] 1. Phase noise (PHN):

[0086] Due to their abundant frequency resources, high-frequency bands (6GHz and above, primarily including 28GHz, 39GHz, 60GHz, and 73GHz) have become a hot research and development topic in the industry, addressing growing communications needs. Their notable features include wide bandwidth and highly integrated antenna arrays for high throughput, but they also present significant issues with mid-range and RF distortion, such as phase noise and carrier frequency offset (CFO). Furthermore, high frequencies also experience greater Doppler shift. All three factors can introduce phase errors, leading to performance degradation or even inoperability of high-frequency communication systems.

[0087] Taking phase noise as an example, as the frequency band increases, the higher the phase noise power spectral density, the greater the impact on the received signal. For example, as shown in Figure 4, Figure 4 is a schematic diagram of the impact of phase noise on the received signal. The left figure of Figure 4 is the received signal after phase noise compensation, and the right figure of Figure 4 is the uncompensated received signal. When the frequency band is high, the deterioration of phase noise will lead to poor demodulation performance. Therefore, the existing new radio (NR) protocol introduces a phase tracking reference signal (PTRS) for both waveforms (cyclic prefix-orthogonal frequency division multiplexing (CP-OFDM) and DFT-s-OFDM) to compensate for the impact of phase noise and improve the demodulation performance under phase noise conditions.

[0088] The effect of phase noise can be expressed as: Where x(n) is the transmitted signal, and y(n) is the received signal. n = 0, 1, ..., N-1, where n represents the time domain sampling point. Simply put, a random phase value is generated at each sampling point n. A significant non-ideal effect associated with high-frequency transmission is phase noise. In the time domain, phase noise manifests itself as a phase offset from the standard constellation points. Existing protocols use a phase tracking reference signal to estimate and compensate for phase noise.

[0089] 2. Discrete Fourier Transform spreading OFDM (DFT-s-OFDM):

[0090] DFT-s-OFDM is the signal generation method for LTE's uplink. Because DFT-s-OFDM performs an additional discrete Fourier transform (DFT) process before traditional OFDM, it can also be called linear precoding OFDM technology.

[0091] As shown in Figure 5, Figure 5 is a schematic diagram of the processing flow of the DFT-s-OFDM technology. The transmitter performs serial-to-parallel conversion, N-point discrete Fourier transform (DFT), subcarrier mapping, M-point inverse discrete Fourier transform (IDFT), parallel-to-serial conversion, adds a cyclic prefix (CP), and performs digital-to-analog conversion (DAC) on the discrete time-domain sequence. The signal is then transmitted through the antenna port and channel. When the receiver receives the signal through the channel and antenna port, it performs analog-to-digital conversion (ADC), removes the cyclic prefix, performs serial-to-parallel conversion, M-point DFT, removes subcarrier mapping, N-point IDFT, and parallel-to-serial conversion to obtain the discrete time-domain sequence.

[0092] DFT-s-OFDM is still essentially a single-carrier network. Physically speaking, the DFT-mapping-inverse fast Fourier transform (IFFT) operation is essentially equivalent to convolving the input signal with a sinc waveform before the DFT. Because it is still a single-carrier network, DFT-s-OFDM has a lower PAPR than OFDM, thereby improving the power transmission efficiency of mobile terminals, extending battery life, and reducing terminal costs.

[0093] 3. SC-OQAM / DFT-s-OFDM with FTSS (two equivalent implementations):

[0094] SC-OQAM is not an implementation method specified in the 3rd Generation Partnership Project (3GPP) protocol, while DFT-S-OFDM is a protocol-defined implementation method. Future protocols may define SC-OQAM or DFT-S-OFDM with FTSS. However, these two implementations are essentially equivalent and both can reduce the PAPR of the DFT-S-OFDM waveform. Therefore, these two implementations are considered alternative waveform technologies for future mobile communications (6G+) and high-frequency scenarios.

[0095] First, SC-OQAM (time domain implementation of DFT-S-OFDM with FTSS):

[0096] As shown in Figure 6, Figure 6 is a schematic diagram of SC-OQAM signal processing. The transmitter first processes the modulated complex signal to obtain real and imaginary signals. Then, it upsamples the real signal and upsamples and delays the imaginary signal by T / 2. The two signals are combined, and finally, the combined signal is pulse shaped and downsampled. As shown in Figure 7, Figure 7 is a schematic diagram of SC-QAM signal processing. The transmitter sequentially modulates, upsamples, pulse shapes, and downsamples the signal.

[0097] It can be seen that the difference between SC-OQAM and SC-QAM is that SC-OQAM separates the real and imaginary parts of the complex modulated signal and then delays one of the signals by T / 2. The other steps are the same.

[0098] Figure 8 shows a schematic diagram of an SC-QAM waveform. SC-QAM carries a complex signal (such as a QAM signal). Taking a root-raised cosine (RRC) filter as an example, the waveform of SC-QAM is complex orthogonal. Complex orthogonality means that an SC-QAM waveform carries a complex signal, and the waveform is orthogonal to the next waveform carrying the signal (i.e., the waveform is zero at the sampling point of the next waveform carrying the signal).

[0099] As shown in Figure 9, Figure 9 is a schematic diagram of an SC-OQAM waveform. When SC-QAM modulation becomes SC-OQAM modulation, the complex orthogonal relationship changes to a partial orthogonal relationship of the real and imaginary parts, and the partial orthogonal relationship means partial interference. Among them, the partial orthogonal relationship means: an SC-OQAM waveform carries a signal with separated real and imaginary parts. Since the relationship between one waveform and the waveform carrying the next signal is non-orthogonal (that is, the waveform is not 0 at the sampling point of the next waveform carrying the signal), but since the information carried by the waveform carrying the next signal is orthogonal, the interference is orthogonal with respect to the signal. This waveform and the next two waveforms carrying signals are in an orthogonal relationship. Therefore, it is orthogonal to the next two signals.

[0100] Due to the partial orthogonality, the receiver discards the imaginary part when receiving a real signal and the real part when receiving an imaginary signal. This allows for accurate information transmission. The benefit of orthogonality between the real and imaginary parts is that the peaks of the real waveform overlap the non-peaks of the imaginary signal. This staggered peaking method effectively reduces PAPR.

[0101] DFT-s-OFDM with FTSS (frequency domain implementation of SC-OQAM):

[0102] As shown in Figure 10, Figure 10 is a schematic diagram of DFT-S-OFDM with FTSS signal processing. The transmitter splits the QAM constellation points used in the DFT-S-OFDM system into real signals and imaginary signals (it may also be directly defined that the input is a PAM signal instead of a QAM signal). Then it performs two times upsampling, that is, the real signal becomes [X, 0, X, 0, X, 0, ...], and the imaginary signal becomes [jY, 0, jY, 0, jY, 0, ...], and then a time delay is performed on the imaginary signal, and the imaginary signal becomes [0, jY, 0, jY, 0, jY, ...], and after merging, it becomes [X, jY, X, jY, X, jY, ...], and the total length of the merged signal becomes twice that of the original complex modulated signal. The symbols after phase rotation / real and imaginary part separation are then subjected to a 2N-point DFT transformation. It should be noted that the above signal processing method is only a special case, and it can also be split into two complex signals, as long as the phase difference between one signal and the other signal satisfies That's it.

[0103] Then, frequency domain truncate spectrum shaping (FTSS) is performed on the DFT signal after 2N points. The specific method is as follows: For the downlink transmission direction, the terminal device receives the transmission resources and FTSS parameters configured or indicated by the network device. The FTSS parameters include one or more of the resource bandwidth and center frequency, modulation mode, original signal bandwidth, filter type, and filter parameters. The resource bandwidth is the bandwidth and center frequency of the signal received by the terminal device. Frequency filtering is performed based on the indicated signal bandwidth and filter parameters.

[0104] As shown in Figure 11, Figure 11 is a schematic diagram of DFT-S-OFDM with FTSS filtering. First, due to the real and imaginary part separation of QAM constellation modulation, the signal length is twice that of traditional QAM constellation modulation, and the DFT length (size) is also twice the DFT size of QAM constellation modulation. The signal after DFT has a characteristic, that is, the spectrum has a conjugate symmetric characteristic: s[n] = s *[Nn], which is A and flip (Filp) (A*) shown in the figure, where A* represents conjugate. Therefore, the data after DFT is actually redundant. Therefore, a truncated frequency domain filter can be performed on the redundant signal. Truncation means that the bandwidth of the filter is smaller than the bandwidth after DFT. For example, if the bandwidth after DFT is 100RB, the frequency domain filter can be designed to be 60RB long. The filtering process is to directly multiply the frequency domain filter with the signal after DFT. Since the signal itself is redundant, the truncated filtering will not cause performance loss. Finally, after the IFFT transform, the CP is added and the signal is sent.

[0105] In summary, the essence of SC-OQAM or DFT-S-OFDM with FTSS is to separate the real and imaginary components and then pass them through a shaping filter. This implementation achieves lower PAPR compared to traditional complex number implementations, primarily because it staggers the overlapping patterns of the separated real and imaginary components.

[0106] In the 5G high-frequency scenario, the DFT-S-OFDM waveform of the existing protocol introduces PTRS to estimate and compensate for phase noise. As shown in Figure 12, Figure 12 is a schematic diagram of the PTRS pattern of DFT-s-OFDM. Each grid in the figure represents a sampling point, that is, a QAM symbol, π / 2BPSK symbol or QPSK symbol (unless otherwise specified below, this explanation applies to all similar figures). The parameters of the pattern include the number of PTRS groups N and the number of sampling points in the group (number of samples per PT-RS group) M, that is, the total number of PTRS is N*M, and the specific mapping position is related to these two parameters and the scheduling bandwidth.

[0107] When the number of sampling points in a group is M = 2, the scheduling bandwidth is evenly divided into N segments or N intervals, and a PTRS group is mapped in the middle of each segment, as shown in the first and third rows of Figure 12. When the number of sampling points in a group is M = 4, the scheduling bandwidth is evenly divided into N segments or N intervals, and a PTRS group is mapped to each segment or interval. The PTRS group of the first segment is mapped at the head of the first segment, the PTRS group of the Nth segment is mapped at the end of the Nth segment, and the PTRS groups of other segments (intervals) are mapped in the middle, as shown in the second, fourth, and fifth rows of Figure 12 (there are only two segments in this case, so there is no PTRS group mapped in the middle of a segment).

[0108] During transmission, these two parameters are implicitly determined by the current scheduling bandwidth based on a preconfigured mapping relationship (the relationship between scheduling bandwidth and parameters, as shown in Table 1, where NRB0 to NRB4 are preconfigured values). For the same terminal device and the same network equipment (same frequency and subcarrier spacing), the scheduling bandwidths corresponding to the five sets of parameters in Figure 12 show a monotonically increasing trend.

[0109] Table 1

[0110] When the modulation method of the transmitted signal changes from the traditional QAM constellation points to the low PAPR OQAM modulation, the impact of phase noise cannot be estimated by separating the real and imaginary parts for the following reasons:

[0111] Assuming there is no phase noise, the received signal can be expressed as follows from the introduction of the SC-OQAM principle:

[0112] Here, x represents the received signal, P is the real signal, and ISI stands for inter-symbol interference. That is, for a transmitted real signal, interference is reflected in the imaginary part. Therefore, the imaginary part can be discarded to demodulate the real signal P. The presence of a summation term is due to the fact that the interference of a waveform may have multiple-order components. As shown in Figure 13, Figure 13 is a schematic diagram of waveform interference of a filter. Waveform interference includes first-order interference components and second-order interference components. This means that it has a value not only for the most recent real signal, but also for the next real signal and the next X real signals. This length is related to the waveform roll-off design and does not constrain the waveform design here.

[0113] However, when phase noise is present, the received signal can be expressed as:

[0114] Phase noise will cause the pure imaginary signal to leak into the real part. By performing Euler expansion on the above formula, we can know that:

[0115] Therefore, the real part becomes Because both the interference term and phase noise are unknown, it is impossible to separate the interference from the signal, resulting in performance loss. Figure 14 shows a performance comparison diagram. The left figure shows the SC-OQAM constellation points without phase noise, while the right figure shows the SC-OQAM constellation points with phase noise.

[0116] In order to solve the above technical problems, the embodiments of the present application provide the following solutions.

[0117] As shown in FIG15 , FIG15 is a flow chart of a communication method provided in an embodiment of the present application. The method mainly includes the following steps:

[0118] S1501: A network device generates a first signal, wherein the first signal includes a first signal and a second signal, wherein the first signal includes X first data signals. The second signal path includes Y second data signals and M first phase noise tracking pilot signals PTRS. The second data signal is The first PTRS is The θ1 belongs to [0,2π), the θ2 belongs to [0,2π), The M first PTRSs are used to process phase noise, the first signal and the second signal are continuously interleaved, X, Y, M and N are all integers greater than or equal to 1, and a, b and c are all real numbers.

[0119] The first signal may be an SC-OQAM signal or a DFT-S-OFDM with FTSS signal. The first signal includes a first signal and a second signal. The first signal or the second signal may include the following forms:

[0120] In one implementation, the X first data signals included in the first signal path are real signals. For example, when θ1=0, the X first data signals are real signals. The Y second data signals included in the second signal path are imaginary signals. For example, when When the Y second data signals are imaginary signals, the first data signal and the second data signal are orthogonal. When the first data signal is a real signal and the second data signal is an imaginary signal, the M first PTRSs included in the first signal are real pilot signals, and the first PTRSs are orthogonal to the second data signal.

[0121] In another implementation, the X first data signals included in the first signal path are imaginary signals. For example, when When θ2 = 0, the X first data signals are imaginary signals. The Y second data signals included in the second signal path are real signals. For example, when θ2 = 0, the Y second data signals are real signals, and the first data signals and the second data signals are orthogonal. When the first data signal is an imaginary signal and the second data signal is a real signal, the M first PTRS included in the second signal path are imaginary pilot signals, and the first PTRS are orthogonal to the second data signal.

[0122] In another implementation, the X first data signals included in the first signal path may be complex signals, the Y first data signals included in the second signal path may also be complex signals, and the M first PTRS included in the second signal path may also be complex pilot signals. The phase difference between the first data signal and the second data signal is The phase difference between the first PTRS and the second data signal is

[0123] The first signal can be set by continuous interleaving between the first signal and the second signal. The continuous interleaving setting can be expressed as: the first data in the first signal is set at the first position in the first signal, the first data in the second signal is set at the second position in the first signal, the second data in the first signal is set at the third position in the first signal, the second data in the second signal is set at the fourth position in the first signal, the third data in the first signal is set at the fifth position in the first signal, ..., and so on. The following explanation assumes that the first data signal is a real signal, the second data signal is an imaginary signal, and the first PTRS is a real pilot signal.

[0124] For example, the first signal is [1, 1j, 1, 1j, 1, -j, -1, j], and the first signal is numbered as [1, 2, 3, 4, 5, 6, ...]. Of course, there are many ways to number, and other numbering methods can also be used. The [1, 3, 5, 7, ...]th signal is called the I-path, and the data signal it carries is the I-path (real) signal, and the I-path signal is [1, 1, 1, -1]. The [2, 4, 6, 8, ...]th signal is called the Q-path, and the data signal it carries is the Q-path (imaginary) signal, and the Q-path signal is [1j, 1j, -j, j]. The Q-path signal also includes the first PTRS, which is a real pilot signal. For example, the first PTRS is 1, and the first PTRS is set at the second position in the Q-path signal, that is, the fourth position of the first signal. The imaginary signal (1j) at the fourth position in the first signal is replaced with 1, and the first signal is adjusted to [1, 1j, 1, 1, 1, -j, -1, j].

[0125] Among them, in the first signal, the sign polarity of the first PTRS is the same as the sign polarity of the adjacent data or data with an even interval, and the sign polarity of the first PTRS is opposite to the sign polarity of the data with an odd interval. The same sign polarity means that they belong to imaginary signals or real signals at the same time, and opposite sign polarity means that they do not belong to real signals or imaginary signals at the same time. For example, in the first signal [1, 1j, 1, 1, 1, -j, -1, j], the first PTRS is 1, which is a real signal, and the adjacent data or data with an even interval are [1, 1, 1, -1], which are all real signals and have the same sign polarity as the first PTRS. The data with an odd interval are [1j, -j, j], which are all imaginary signals and have the opposite sign polarity as the first PTRS.

[0126] Optionally, the positive and negative phases of the first PTRS are determined based on the positive and negative phases of the interference of the data carried by the first signal on the first PTRS. Furthermore, the positive and negative phases of the first PTRS are the same as the positive and negative phases of the interference of the data carried by the first signal on the first PTRS. For example, if the total interference of the data carried by the first signal on the first PTRS is 0.2, the first PTRS can select a positive phase. For another example, if the first PTRS is 1, the sum of the interference of the first PTRS and the data carried by the first signal on the first PTRS is 1.2, so that the energy of the first PTRS is maximized. Optionally, since it is relatively complicated to calculate the interference of all the data carried by the first signal on the first PTRS, the positive and negative phases of the first PTRS can be determined based on the positive and negative phases of the data adjacent to the first PTRS. The positive and negative phases of the first PTRS are the same as the positive and negative phases of the adjacent data.

[0127] Optionally, the first signal further includes M second PTRSs, one second PTRS corresponds to one first PTRS, and the second PTRS is The M second PTRSs are used to carry data, and the M second PTRSs are not used to process phase noise. The d is a real number. That is, the first PTRS is a real pilot signal, and the second PTRS is an imaginary pilot signal; or the first PTRS is an imaginary pilot signal, and the second PTRS is a real pilot signal. The first PTRS is orthogonal to the second PTRS, or the phase difference between the first PTRS and the second PTRS is

[0128] Optionally, the second PTRS is adjacent to the first PTRS. This facilitates adjusting the positive and negative phases of the second PTRS in the first signal to more closely match its impact on the first PTRS in the second signal. Furthermore, the positive and negative phases of the second PTRS are identical to those of the first PTRS, ensuring that the positive and negative phases of the interference of the second PTRS on the first PTRS are identical to those of the first PTRS, thereby maximizing the energy of the first PTRS.

[0129] For example, as shown in Figure 16, Figure 16 is a schematic diagram of a first signal. The first signal includes a first signal and a second signal. The first signal includes four real signals and one imaginary pilot signal I. The four real signals are located at positions #1, #5, #7, and #9 in the first signal, respectively, and the imaginary pilot signal I is located at position #3 in the first signal. The second signal includes three imaginary signals and one real pilot signal Q. The three imaginary signals are located at positions #2, #6, and #8 in the first signal, respectively, and the real pilot signal Q is located at position #4 in the first signal. The first signal and the second signal are interleaved continuously. One imaginary pilot signal I corresponds to one real pilot signal Q, and the imaginary pilot signal I is adjacent to the real pilot signal Q. The imaginary pilot signal I is used to carry data, and the real pilot signal Q is used to mitigate phase noise. Figure 16 only shows the PTRS pattern for one group of signals. The PTRS patterns for other groups are similar and will not be repeated here.

[0130] It should be noted that if the first PTRS exists in the second signal but the second PTRS does not exist in the first signal, the second PTRS can be considered a data signal. The positive and negative phases of the data signal are the same as the positive and negative phases of the interference caused by other data in the first signal on the first PTRS. The data signal can be the data signal at the index position before the first PTRS in the first signal, or the data signal on the first signal at the index position after the first PTRS in the first signal.

[0131] Optionally, the M first PTRSs are evenly spaced in the second signal. That is, if the second signal includes multiple first PTRSs, the multiple first PTRSs are evenly spaced in the second signal. Optionally, an odd number of data may be separated between two consecutive first PTRSs in the second signal. Where a second PTRS is adjacent to a first PTRS, the positive and negative phases of the interference caused by the second PTRS on the first PTRS are the same as the positive and negative phases of the interference caused by the data adjacent to the second PTRS on the second PTRS.

[0132] For example, as shown in Figure 17, Figure 17 is a schematic diagram of another first signal. The first signal includes a first signal and a second signal. The first signal includes two real signals and two imaginary pilot signals I. The two real signals are located at positions #3 and #5 in the first signal, respectively, and the two imaginary pilot signals I are located at positions #1 and #7 in the first signal, respectively. The second signal includes one imaginary signal and two real pilot signals Q. One imaginary signal is located at position #4 in the first signal, and the two real pilot signals Q are located at positions #2 and #6 in the first signal, respectively. One imaginary pilot signal I is adjacent to one real pilot signal Q. The two imaginary pilot signals I are not used for phase noise processing at the receiving end, while the two real pilot signals Q are used for phase noise processing at the receiving end.

[0133] Due to the interference characteristics of the filter, the interference effects of the data at position #1 on position #2, position #4, and position #6 are 0.6, -0.16, and 0.05, respectively. Generally speaking, the influence of the filter is positive, negative, positive, and negative. The influence of odd orders is positive, and the influence of even orders is negative. Therefore, in order to ensure the consistency of the influence of the data on the two real pilot signals Q, for example, the consistency of the influence of the data at position #1 on the real pilot signal Q at position #2 and the real pilot signal Q at position #6 (both are positive phases), the two real pilot signals Q in the second signal are set at equally spaced positions in the second signal, with one data interval in the middle. In addition, an imaginary pilot signal I is adjacent to a real pilot signal Q, so as to facilitate the adjustment of the positive and negative phases of the two imaginary pilot signals I in the first signal, so as to better match the influence on the two real pilot signals Q in the second signal. Figure 17 only shows the PTRS pattern of one group of signals. The PTRS patterns for other groups are so similar that they will not be repeated here.

[0134] S1502: The network device sends a first signal to the terminal device.

[0135] Optionally, the network device may send a predefined PTRS pattern to the terminal device, where the PTRS pattern is used to determine PTRS parameters, wherein the PTRS parameters may include the number N of PTRS groups and the number M of sampling points within the group.

[0136] S1503: The terminal device processes the phase noise based on the M first PTRSs.

[0137] Specifically, the terminal device can determine the current scheduling bandwidth, determine the PTRS parameters corresponding to the PTRS pattern based on the current scheduling bandwidth, determine the mapping position of the first PTRS in the first signal based on the PTRS parameters, obtain the first PTRS at the mapping position in the first signal, and process the phase noise through the first PTRS.

[0138] In the embodiment of the present application, the first signal and the second signal are continuously interleaved, and the phase angle between the first signal and the second signal satisfies A first pilot signal reception (PTRS) is set in the second signal to process phase noise. For example, if the first signal is a real signal, a real pilot signal is set in the second signal's place where the imaginary signal was originally set. This ensures that the interference of the data carried by the first signal on the first PTRS is in the same direction as the first PTRS, maximizing the signal energy of the first PTRS. Phase noise is processed using the first PTRS, improving the accuracy of phase noise processing.

[0139] It can be understood that in the above-mentioned method embodiments, the methods and operations implemented by the terminal device can also be implemented by components that can be used for the terminal device (such as chips or circuits), and the methods and operations implemented by the network device can also be implemented by components that can be used for the network device (such as chips or circuits).

[0140] In the embodiment of the present application, the terminal device or network device can be divided into functional modules according to the above method example. For example, each functional module can be divided corresponding to each function, or two or more functions can be integrated into one processing module. The above-mentioned integrated modules can be implemented in the form of hardware or in the form of software functional modules. It should be noted that the division of modules in the embodiment of the present application is schematic and is only a logical functional division. There may be other division methods in actual implementation. The following is an example of dividing each functional module corresponding to each function.

[0141] The method provided in the embodiment of the present application is described in detail above in conjunction with Figure 15. Below, the communication device provided in the embodiment of the present application is described in detail in conjunction with Figures 18 and 19. It should be understood that the description of the device embodiment corresponds to the description of the method embodiment. Therefore, for matters not described in detail, please refer to the method embodiment above. For the sake of brevity, it will not be repeated here.

[0142] Please refer to Figure 18, which is a schematic diagram of the structure of a communication device provided in an embodiment of the present application. The communication device may include a processing module 1801 and a sending module 1802.

[0143] The communication device can implement the steps or processes corresponding to those performed by the network device in the above method embodiments. For example, it can be a network device, or a chip or circuit configured in the network device. The sending module 1802 is used to perform the sending and receiving related operations on the network device side of the above method embodiments, and the processing module 1801 is used to perform the processing related operations of the network device in the above method embodiments.

[0144] The processing module 1801 is configured to generate a first signal, wherein the first signal includes a first signal and a second signal, wherein the first signal includes X first data signals. The second signal path includes Y second data signals and M first phase noise tracking pilot signals PTRS. The second data signal is The first PTRS is The θ1 belongs to [0,2π), the θ2 belongs to [0,2π), The M first PTRSs are used to process phase noise, the first signal and the second signal are continuously interleaved, X, Y, M, and N are all integers greater than or equal to 1, and a, b, and c are all real numbers;

[0145] The sending module 1802 is configured to send a first signal to a terminal device.

[0146] Optionally, the positive and negative phases of the first PTRS are determined according to the positive and negative phases of interference caused by data carried by the first signal on the first PTRS.

[0147] Optionally, the positive and negative phases of the first PTRS are the same as the positive and negative phases of interference caused by data carried by the first signal on the first PTRS.

[0148] Optionally, the first signal further includes M second PTRSs, one second PTRS corresponds to one first PTRS, and the second PTRS is The M second PTRSs are used to carry data, and d is a real number.

[0149] Optionally, the positive and negative phases of the second PTRS are the same as the positive and negative phases of the first PTRS.

[0150] Optionally, the second PTRS is adjacent to the first PTRS.

[0151] Optionally, the M first PTRSs are arranged at equal intervals in the second signal.

[0152] Optionally, the sending module 1802 is further configured to send a predefined PTRS pattern to the terminal device, where the PTRS pattern is used to determine PTRS parameters.

[0153] It should be noted that the implementation of each module can also correspond to the corresponding description of the method embodiment shown in Figure 15, and execute the methods and functions executed by the network device in the above embodiment.

[0154] 19 is a schematic diagram of the structure of another communication device provided in an embodiment of the present application. The communication device may include a receiving module 1901 and a processing module 1902.

[0155] The communication device can implement the steps or processes corresponding to those performed by the terminal device in the above method embodiments. For example, it can be a terminal device, or a chip or circuit configured in the terminal device. The receiving module 1901 is used to perform the transmission and reception related operations on the terminal device side of the above method embodiments, and the processing module 1902 is used to perform the processing related operations of the terminal device in the above method embodiments.

[0156] The receiving module 1901 is configured to receive a first signal sent by a network device, wherein the first signal includes a first signal and a second signal, wherein the first signal includes X first data signals. The second signal path includes Y second data signals and M first phase noise tracking pilot signals PTRS. The second data signal is The first PTRS is The θ1 belongs to [0,2π), the θ2 belongs to [0,2π), The M first PTRSs are used to process phase noise, the first signal and the second signal are continuously interleaved, X, Y, M, and N are all integers greater than or equal to 1, and a, b, and c are all real numbers;

[0157] The processing module 1902 is configured to process the phase noise based on the M first PTRSs.

[0158] Optionally, the positive and negative phases of the first PTRS are determined according to the positive and negative phases of interference caused by data carried by the first signal on the first PTRS.

[0159] Optionally, the positive and negative phases of the first PTRS are the same as the positive and negative phases of interference caused by data carried by the first signal on the first PTRS.

[0160] Optionally, the first signal further includes M second PTRSs, one second PTRS corresponds to one first PTRS, and the second PTRS is The M second PTRSs are used to carry data, and d is a real number.

[0161] Optionally, the positive and negative phases of the second PTRS are the same as the positive and negative phases of the first PTRS.

[0162] Optionally, the second PTRS is adjacent to the first PTRS.

[0163] Optionally, the M first PTRSs are arranged at equal intervals in the second signal.

[0164] Optionally, the receiving module 1901 is further configured to receive a predefined PTRS pattern sent by the network device, where the PTRS pattern is used to determine PTRS parameters.

[0165] It should be noted that the implementation of each module can also correspond to the corresponding description of the method embodiment shown in Figure 15 to execute the methods and functions executed by the terminal device in the above embodiment.

[0166] Figure 20 is a schematic diagram of the structure of a network device provided in an embodiment of the present application. The network device can be applied to the system shown in Figure 1 to perform the functions of the network device in the above method embodiment, or to implement the steps or processes performed by the network device in the above method embodiment.

[0167] As shown in Figure 20, the network device includes a processor 2001 and a transceiver 2002. Optionally, the network device also includes a memory 2003. The processor 2001, the transceiver 2002, and the memory 2003 can communicate with each other via internal connection paths to transmit control and / or data signals. The memory 2003 is used to store computer programs, and the processor 2001 is used to call and execute the computer programs from the memory 2003 to control the transceiver 2002 to transmit and receive signals. Optionally, the network device may also include an antenna for transmitting uplink data or uplink control signaling output by the transceiver 2002 via wireless signals.

[0168] The processor 2001 and the memory 2003 may be combined into a processing device, and the processor 2001 is configured to execute program code stored in the memory 2003 to implement the aforementioned functions. In a specific implementation, the memory 2003 may also be integrated into the processor 2001 or independent of the processor 2001. The processor 2001 may correspond to the processing module in FIG18 .

[0169] The transceiver 2002 may correspond to the transmitting module in FIG18 and may also be referred to as a transceiver unit or a transceiver module. The transceiver 2002 may include a receiver (or receiver, receiving circuit) and a transmitter (or transmitter, transmitting circuit). The receiver is used to receive signals, and the transmitter is used to transmit signals.

[0170] It should be understood that the network device shown in FIG20 is capable of implementing each process related to the network device in the method embodiment shown in FIG15 . The operations and / or functions of each module in the network device are respectively for implementing the corresponding processes in the above method embodiment. For details, please refer to the description of the above method embodiment. To avoid repetition, detailed description is omitted here.

[0171] The processor 2001 can be used to execute the actions implemented within the network device described in the previous method embodiments, while the transceiver 2002 can be used to execute the actions of the network device sending to or receiving from the terminal device described in the previous method embodiments. For details, please refer to the description of the previous method embodiments and will not be repeated here.

[0172] Processor 2001 may be a central processing unit (CPU), a general-purpose processor (GPOR), a digital signal processor (DSP), an application-specific integrated circuit (ASIC), a field-programmable gate array (FPGA), or other programmable logic device (PLD), a transistor logic device (TLD), a hardware component, or any combination thereof. It may implement or execute the various exemplary logic blocks, modules, and circuits described in conjunction with the disclosure of this application. Processor 2001 may also be a combination that implements computing functions, such as a combination of one or more microprocessors, a combination of a DSP and a microprocessor, and so on. Communication bus 2004 may be a Peripheral Component Interconnect (PCI) bus or an Extended Industrial Standard Architecture (EISA) bus. These buses may be categorized as address buses, data buses, control buses, and so on. For ease of illustration, FIG20 shows only one bold line, but this does not imply that there is only one bus or type of bus. Communication bus 2004 is used to connect and communicate between these components. In the embodiment of this application, transceiver 2002 is used to communicate signaling or data with other node devices. The memory 2003 may include volatile memory, such as nonvolatile dynamic random access memory (NVRAM), phase change random access memory (PRAM), magnetoresistive random access memory (MRAM), etc. It may also include non-volatile memory, such as at least one disk storage device, electrically erasable programmable read-only memory (EEPROM), flash memory devices, such as NOR flash memory or NAND flash memory, semiconductor devices, such as solid state disks (SSDs), etc. The memory 2003 may optionally be at least one storage device located away from the aforementioned processor 2001. The memory 2003 may optionally also store a set of computer program code or configuration information. Optionally, the processor 2001 may also execute the program stored in the memory 2003. The processor may cooperate with the memory and the transceiver to execute any of the methods and functions of the network device in the above-mentioned application embodiments.

[0173] Figure 21 is a schematic diagram of the structure of a terminal device provided in an embodiment of the present application. The terminal device can be applied to the system shown in Figure 1 to perform the functions of the terminal device in the above method embodiment, or to implement the steps or processes performed by the terminal device in the above method embodiment.

[0174] As shown in Figure 21, the terminal device includes a processor 2101 and a transceiver 2102. Optionally, the terminal device also includes a memory 2103. The processor 2101, transceiver 2102, and memory 2103 can communicate with each other via internal connection paths to transmit control and / or data signals. The memory 2103 is used to store computer programs, and the processor 2101 is used to call and execute the computer programs from the memory 2103 to control the transceiver 2102 to send and receive signals. Optionally, the terminal device may also include an antenna for transmitting uplink data or uplink control signaling output by the transceiver 2102 via wireless signals.

[0175] The processor 2101 and the memory 2103 may be combined into a processing device, and the processor 2101 is configured to execute program code stored in the memory 2103 to implement the aforementioned functions. In a specific implementation, the memory 2103 may also be integrated into the processor 2101 or independent of the processor 2101. The processor 2101 may correspond to the processing module in FIG19 .

[0176] The transceiver 2102 may correspond to the receiving module in FIG19 and may also be referred to as a transceiver unit or transceiver module. The transceiver 2102 may include a receiver (or receiver, receiving circuit) and a transmitter (or transmitter, transmitting circuit). The receiver is used to receive signals, and the transmitter is used to transmit signals.

[0177] It should be understood that the terminal device shown in FIG21 is capable of implementing the various processes involved in the terminal device in the method embodiment shown in FIG15 . The operations and / or functions of the various modules in the terminal device are respectively for implementing the corresponding processes in the above method embodiment. For details, please refer to the description of the above method embodiment. To avoid repetition, detailed description is omitted here.

[0178] The processor 2101 can be used to execute the actions implemented within the terminal device described in the previous method embodiments, while the transceiver 2102 can be used to execute the actions of the terminal device sending to or receiving from the network device described in the previous method embodiments. For details, please refer to the description of the previous method embodiments and will not be repeated here.

[0179] The processor 2101 can be any of the aforementioned types of processors. The communication bus 2104 can be a PCI bus or an EISA bus, for example. These buses can be divided into address buses, data buses, and control buses. For ease of illustration, Figure 21 shows only one thick line, but this does not imply that there is only one bus or one type of bus. The communication bus 2104 is used to enable communication between these components. The transceiver 2102 of the device in the embodiments of the present application is used to communicate signaling or data with other devices. The memory 2103 can be any of the aforementioned types of memory. The memory 2103 can optionally be at least one storage device located remotely from the processor 2101. The memory 2103 stores a set of computer program code or configuration information, and the processor 2101 executes the program in the memory 2103. The processor can cooperate with the memory and transceiver to perform any of the methods and functions of the terminal device in the aforementioned embodiments.

[0180] An embodiment of the present application also provides a chip system, which includes a processor for supporting a terminal device or a network device to implement the functions involved in any of the above embodiments, such as generating or processing the first signal involved in the above method.

[0181] In one possible design, the chip system may also include a memory for storing computer programs and data necessary for the terminal device or network device. The chip system may consist of a single chip or may include a chip and other discrete components. The inputs and outputs of the chip system correspond to the receive and transmit operations of the terminal device or network device in the method embodiment, respectively.

[0182] According to the method provided in the embodiments of the present application, the present application also provides a computer program product, which includes: a computer program, which, when running on a computer, enables the computer to execute the method of any one of the embodiments shown in Figure 15.

[0183] According to the method provided in the embodiments of the present application, the present application also provides a computer-readable medium, which stores a computer program. When the computer program runs on a computer, the computer executes the method of any one of the embodiments shown in Figure 15.

[0184] According to the method provided in the embodiment of the present application, the present application also provides a communication system, which includes one or more terminal devices and one or more network devices as mentioned above.

[0185] In the above embodiments, all or part of the embodiments may be implemented by software, hardware, firmware, or any combination thereof. When implemented using software, all or part of the embodiments may be implemented in the form of a computer program product. The computer program product includes one or more computer instructions. When the computer instructions are loaded and executed on a computer, all or part of the processes or functions described in the embodiments of the present application are generated. The computer may be a general-purpose computer, a special-purpose computer, a computer network, or other programmable device. The computer instructions may be stored in a computer-readable storage medium or transmitted from one computer-readable storage medium to another computer-readable storage medium. For example, the computer instructions may be transmitted from one website, computer, server, or data center to another website, computer, server, or data center via a wired (e.g., coaxial cable, optical fiber, digital subscriber line (DSL)) or wireless (e.g., infrared, wireless, microwave, etc.) method. The computer-readable storage medium may be any available medium that a computer can access or a data storage device such as a server or data center that includes one or more available media integrated therein. The available medium may be a magnetic medium (eg, a floppy disk, a hard disk, a magnetic tape), an optical medium (eg, a high-density digital video disc (DVD)), or a semiconductor medium (eg, a solid state disc (SSD)).

[0186] The above description is merely a specific embodiment of the present application, but the scope of protection of the present application is not limited thereto. Any changes or substitutions that can be easily conceived by a person skilled in the art within the technical scope disclosed in this application should be included in the scope of protection of this application. Therefore, the scope of protection of this application should be based on the scope of protection of the claims.

Claims

1. A communication method, characterized in that: The method comprises: Generate a first signal, the first signal includes a first signal and a second signal, the first signal includes X first data signals, the first data signal is The second signal path includes Y second data signals and M first phase noise tracking pilot signals PTRS, and the second data signal is The first PTRS is The θ1 belongs to [0,2π), the θ2 belongs to [0,2π), The M first PTRSs are used to process phase noise, the first signal and the second signal are continuously interleaved, X, Y, M and N are all integers greater than or equal to 1, and a, b and c are all real numbers; A first signal is sent to a terminal device.

2. The method according to claim 1, characterized in that The positive and negative phases of the first PTRS are determined according to the positive and negative phases of interference of the data carried by the first signal on the first PTRS.

3. The method according to claim 2, characterized in that The positive and negative phases of the first PTRS are the same as the positive and negative phases of interference of the data carried by the first signal on the first PTRS.

4. The method according to any one of claims 1 to 3, characterized in that: The first signal also includes M second PTRSs, one second PTRS corresponds to one first PTRS, and the second PTRS is The M second PTRSs are used to carry data, and d is a real number.

5. The method according to claim 4, characterized in that The positive and negative phases of the second PTRS are the same as those of the first PTRS.

6. The method according to claim 4 or 5, characterized in that The second PTRS is adjacent to the first PTRS.

7. The method according to any one of claims 1 to 6, characterized in that: The M first PTRSs are arranged at equal intervals in the second signal.

8. The method according to any one of claims 1 to 7, characterized in that: The method further comprises: A predefined PTRS pattern is sent to the terminal device, where the PTRS pattern is used to determine PTRS parameters.

9. A communication method, characterized in that: The method comprises: Receive a first signal sent by a network device, the first signal including a first signal and a second signal, the first signal including X first data signals, the first data signal being The second signal path includes Y second data signals and M first phase noise tracking pilot signals PTRS, and the second data signal is The first PTRS is The θ1 belongs to [0,2π), the θ2 belongs to [0,2π), The M first PTRSs are used to process phase noise, the first signal and the second signal are continuously interleaved, X, Y, M and N are all integers greater than or equal to 1, and a, b and c are all real numbers; Based on the M first PTRSs, phase noise is processed.

10. The method according to claim 9, characterized in that The positive and negative phases of the first PTRS are determined according to the positive and negative phases of interference of the data carried by the first signal on the first PTRS.

11. The method according to claim 10, characterized in that The positive and negative phases of the first PTRS are the same as the positive and negative phases of interference of the data carried by the first signal on the first PTRS.

12. The method according to any one of claims 9 to 11, characterized in that: The first signal also includes M second PTRSs, one second PTRS corresponds to one first PTRS, and the second PTRS is The M second PTRSs are used to carry data, and d is a real number.

13. The method according to claim 12, characterized in that The positive and negative phases of the second PTRS are the same as those of the first PTRS.

14. The method according to claim 12 or 13, characterized in that The second PTRS is adjacent to the first PTRS.

15. The method according to any one of claims 9 to 14, characterized in that: The M first PTRSs are arranged at equal intervals in the second signal.

16. The method according to any one of claims 9 to 15, characterized in that: The method further comprises: A predefined PTRS pattern sent by the network device is received, where the PTRS pattern is used to determine a PTRS parameter.

17. A communication device, characterized in that: The communication device comprises a memory and a processor, wherein the memory is used to store a computer program, and the processor runs the computer program to enable the communication device to perform the method according to any one of claims 1 to 8.

18. A communication device, characterized in that: The device comprises a memory and a processor, wherein the memory is used to store a computer program, and the processor runs the computer program to enable the communication device to perform the method according to any one of claims 9 to 16.

19. A computer-readable storage medium, characterized in that: The computer-readable storage medium comprises a computer program, and when the computer program is executed by a processor, the method according to any one of claims 1 to 16 is implemented.

20. A chip, characterized in that: The chip includes a processor and a communication interface, wherein the communication interface is used to communicate with an external device or an internal device, and the processor is used to implement the method according to any one of claims 1-16.

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