Switch-based compact phase shifter and integrated phase shifter

Abstract

The present application relates to the technical field of communications, and in particular to a switch-based compact phase shifter and an integrated phase shifter, which solve the problems of excessive size and costs of existing phase shifters. The switch-based compact phase shifter comprises: a first filter network, the first filter network being an Nth order high-pass filter network; a second filter network, the second filter network being an Mth order low-pass filter network; and a third filter network, the third filter network being an Rth order low-pass filter network; wherein: the first filter network, the second filter network, and the third filter network are connected in parallel by means of a double-pole three-throw switch; and when the second filter network is turned on alone, the insertion phase of the switch-based compact phase shifter is a reference phase; when the third filter network is turned on alone, the insertion phase of the switch-based compact phase shifter is a first phase; when only the first filter network and the second filter network are turned on, the insertion phase of the switch-based compact phase shifter is a second phase; and when only the first filter network and the third filter network are turned on, the insertion phase of the switch-based compact phase shifter is a third phase.

Description

Switching compact phase shifter and integrated phase shifter TECHNICAL FIELD

[0001] The present application relates to the technical field of communication, in particular to a switching compact phase shifter and an integrated phase shifter. BACKGROUND

[0002] With the continuous breakthrough of 5G communication technology, the phased array system has more and more attractive application in the beamforming technology. The phased array system has the characteristics of strong anti-interference ability and high reliability. With the continuous breakthrough of 5G technology, the application of the automobile system in the unmanned driving technology is also more and more popular. In these technologies, the phased array system is a very important link. In the phased array system, the T / R (Transmitter and Receiver) transceiver assembly is the core architecture, and the phase shifter is an important component of the T / R transceiver assembly, which directly affects the performance of the entire phased array system, such as phase shift accuracy, insertion loss, etc. For a passive switching phase shifter, the increase of phase shift accuracy also needs to increase the digital control bits of the phase shifter and the corresponding phase shift units, so the switching phase shifter with high phase shift accuracy often occupies a larger chip area. In passive and active phased arrays, phase shifters are distributed throughout the antenna array, and the increase of the size of a single phase shifter chip will lead to a rapid increase in the cost of the phased array, therefore, reducing the size of the phase shifter chip helps to meet the market demand for miniaturization and low-cost phased arrays. In addition, the phased array system is composed of multiple T / R transceiver assemblies, and each T / R transceiver assembly needs at least one phase shifter, therefore, how to reduce the direct current power consumption of the vector synthesis type phase shifter is of great significance to reduce the power consumption and cost of the entire phased array system.

[0003] SUMMARY

[0004] In view of the above analysis, the embodiments of the present application aim to provide a switching compact phase shifter and an integrated phase shifter to solve the problems of excessive size and high cost of the existing phase shifter.

[0005] In one aspect, the embodiments of the present application provide a switching compact phase shifter, comprising:

[0006] a first filter network, the first filter network being an N-order high-pass filter network;

[0007] a second filter network, the second filter network being an M-order low-pass filter network;

[0008] a third filter network, the third filter network being an R-order low-pass filter network;

[0009] The first filter network, the second filter network, and the third filter network are connected in parallel through a double-pole three-throw switch, and

[0010] When the second filter network is turned on alone, the insertion phase of the switch compact phase shifter is a reference phase;

[0011] When the third filter network is turned on alone, the insertion phase of the switch compact phase shifter is a first phase;

[0012] When the first filter network and the second filter network are turned on alone, the insertion phase of the switch compact phase shifter is a second phase;

[0013] When the first filter network and the third filter network are turned on alone, the insertion phase of the switch compact phase shifter is a third phase.

[0014] Based on the further improvement of the above-mentioned switch compact phase shifter, the double-pole three-throw switch comprises:

[0015] A first switch unit connected in series with the first filter network, which controls the turn-on and turn-off of the first filter network;

[0016] A second switch unit connected in series with the second filter network, which controls the turn-on and turn-off of the second filter network;

[0017] A third switch unit connected in series with the third filter network, which controls the turn-on and turn-off of the third filter network;

[0018] A first power supply end connected to the first switch unit;

[0019] A second power supply end connected to the second switch unit, and connected to the third switch unit through an inverter; wherein

[0020] The first power supply end controls the turn-on and turn-off of the first switch unit, and the second power supply end controls the turn-on and turn-off of the second switch unit and the third unit.

[0021] Based on the further improvement of the above-mentioned switch compact phase shifter, the first switch unit comprises two first transistors, which are respectively located at the input end and the output end of the first filter network; the second switch unit comprises two second transistors, which are respectively located at the input end and the output end of the second filter network; and the third switch unit comprises two third transistors, which are respectively located at the input end and the output end of the third filter network.

[0022] Based on the further improvement of the switch compact phase shifter above, the N, M, R are equal to 3, and the first phase is 11.25°, the second phase is 22.5°, and the third phase is 33.75°.

[0023] Based on the further improvement of the switch compact phase shifter above, the inductance and capacitance parameters in the switch compact phase shifter are determined by the following method:

[0024] The constraint equation for solving the inductance and capacitance parameters is established according to the first phase, the second phase and the third phase; and

[0025] A multi-objective search algorithm based on a particle swarm algorithm is used for iterative calculation to solve the constraint equation until the result converges.

[0026] In another aspect, the embodiments of the present application also provide an integrated phase shifter, comprising:

[0027] a passive switch type phase shifter, a quadrature signal generating network, a variable gain amplifier, a switching switch; wherein,

[0028] The passive switch type phase shifter, the quadrature signal generating network, and the variable gain amplifier are cascaded in sequence.

[0029] The passive switch type phase shifter comprises the switch compact phase shifter according to any one of claims 1 to 5; and

[0030] When the switching switch is switched to be disconnected from the variable gain amplifier, the integrated phase shifter is a passive switch type phase shifter.

[0031] When the switching switch is switched to be connected to the variable gain amplifier, the integrated phase shifter is a passive switch and vector synthesis integrated phase shifter.

[0032] Based on the further improvement of the integrated phase shifter above, the switching switch is cascaded at the output end of the variable gain amplifier, and the switching switch comprises a first switch and a second switch. When the first switch is turned on and the second switch is turned off, the variable gain amplifier is in a working state, and the integrated phase shifter is a passive switch and vector synthesis integrated phase shifter. When the first switch is turned off and the second switch is turned on, the variable gain amplifier stops working, and the integrated phase shifter is a passive switch type phase shifter.

[0033] Based on the further improvement of the integrated phase shifter above, the variable gain amplifier is a variable gain amplifier based on a Gilbert cell.

[0034] Based on the further improvement of the integrated phase shifter above, the passive switch type phase shifter further comprises:

[0035] a first high-low type phase-shifting unit, a second high-low type phase-shifting unit, a bridge-T type phase-shifter based on capacitance or inductance; wherein

[0036] The first high-low type phase-shifting unit, the second high-low type phase-shifting unit, the switch compact phase-shifter, and the bridge-T type phase-shifter based on capacitance or inductance are cascaded in sequence.

[0037] Based on the further improvement of the integrated phase-shifter, the first high-low type phase-shifting unit generates a phase change of 180°, the second high-low type phase-shifting unit generates a phase change of 90°, the switch compact phase-shifter generates phase changes of 11.25°, 22.5° and 33.75°, the bridge-T type phase-shifter based on capacitance or inductance generates a phase change of 45°, and the variable gain amplifier generates a phase change of 0-8.4375° with a step of 2.8125°.

[0038] Compared with the prior art, the present application can at least achieve one of the following beneficial effects:

[0039] 1. The present application innovatively proposes a compact switch type phase-shifting unit based on a double-pole triple-throw switch (DPTTS), which integrates multiple phase-shifting units in the same circuit topology through the DPTTS, so that the area of the corresponding phase-shifting unit is greatly reduced, thereby meeting the demand for miniaturization and low cost of the phase-shifter.

[0040] 2. The present application integrates a passive switch type phase-shifter and a vector synthesis type phase-shifter. The passive switch type phase-shifter has low phase shift accuracy, but has no DC power consumption in ideal conditions. When the phase shift accuracy requirement is high, it is switched to the vector synthesis type phase-shifter, and when the phase shift accuracy requirement is low, it is switched to the passive phase-shifter to reduce power consumption.

[0041] 3. The phase-shifter of the present application exhibits excellent performance in terms of phase shift accuracy, insertion loss, return loss, etc.

[0042] In the present application, the above technical solutions can also be combined with each other to realize more preferred combination solutions. Other features and advantages of the present application will be described in the subsequent specification, and some advantages will become apparent from the specification or be understood through the implementation of the present application. The purpose and other advantages of the present application can be achieved and obtained from the specific indications in the specification and the drawings. BRIEF DESCRIPTION OF DRAWINGS

[0043] The accompanying drawings are included to provide a further understanding of the embodiments, and are incorporated in and constitute a part of this application, and together with the specification illustrate the embodiments, but are not considered as limiting the application, in which the same reference numerals refer to the same or similar components throughout the drawings;

[0044] FIG. 1 is an example circuit topology of a switched compact phase shifter according to an embodiment of the present application.

[0045] FIG. 2 illustrates four conduction states of the circuit topology shown in FIG. 1.

[0046] FIG. 3 illustrates an iterative calculation process of a phase shift unit of the switched compact phase shifter according to an embodiment of the present application.

[0047] FIG. 4 is an example circuit topology of a phase shifter according to an embodiment of the present application.

[0048] FIG. 5a illustrates an example circuit topology of a high / low pass type quadrature signal generation network according to an embodiment of the present application.

[0049] FIG. 5b illustrates an example circuit topology of a high / low pass type 180° phase shift unit according to an embodiment of the present application.

[0050] FIG. 5c illustrates an example circuit topology of a high / low pass type 90° phase shift unit according to an embodiment of the present application.

[0051] FIG. 6 is an example circuit topology of an inductance-based bridge T type phase shift unit according to an embodiment of the present application.

[0052] FIG. 7 illustrates a partial enlarged view of a vector modulation module and a logic control module.

[0053] FIG. 8 is a signal flow line diagram of a 7-bit integrated passive switched and vector synthesized phase shifter according to an embodiment of the present application.

[0054] FIG. 9 is a signal flow line diagram of a 5-bit passive switched phase shifter according to an embodiment of the present application.

[0055] FIGS. 10-11 illustrate performance of a 7-bit integrated passive switched and vector synthesized phase shifter in terms of phase shift accuracy, insertion loss and return loss according to an embodiment of the present application.

[0056] FIGS. 12-13 illustrate performance of a 5-bit integrated passive switched and vector synthesized phase shifter in terms of phase shift accuracy, insertion loss and return loss according to an embodiment of the present application. DETAILED DESCRIPTION

[0057] The preferred embodiments of the present application will be described in detail with reference to the drawings, wherein the same or similar components are denoted by the same reference numerals, and thus repeated description is omitted as appropriate. The preferred embodiments of the present application will be described in detail with reference to the drawings, wherein the same or similar components are denoted by the same reference numerals, and thus repeated description is omitted as appropriate.

[0058] FIG. 1 is an example circuit topology of a switched compact phase shifter according to an embodiment of the present application.

[0059] An embodiment of the present application will be described below with reference to Fig. 1.

[0060] As shown in Fig. 1, the switch-compact phase shifter includes a third-order high-pass filter network composed of two capacitors C 71 and one inductor L 71 , a third-order low-pass filter network (i.e., low-pass filter network I) composed of two capacitors C 72 and one inductor L 72 , and a third-order low-pass filter network (low-pass filter network II) composed of two capacitors C 73 and one inductor L 73 .

[0061] For the convenience of description, the third-order high-pass filter network composed of the capacitors C 71 and the inductor L 71 is referred to as a first filter network, the third-order low-pass filter network composed of the capacitors C 72 and the inductor L 72 is referred to as a second filter network, and the third-order low-pass filter network composed of the capacitors C 73 and the inductor L 73 is referred to as a third filter network.

[0062] The input terminal and the output terminal of the first filter network are connected in series with a switching element M 71 , the input terminal and the output terminal of the second filter network are connected in series with a switching element M 72 , and the input terminal and the output terminal of the third filter network are connected in series with a switching element M 73 . The two switching elements M 71 control the conduction and the cutoff of the first filter network, the two switching elements M 72 control the conduction and the cutoff of the second filter network, and the two switching elements M 73 control the conduction and the cutoff of the third filter network.

[0063] The switch-compact phase shifter further includes power supply terminals V A and V B , the power supply terminal V A is connected to the gate of the two switching elements M 71 , the power supply terminal V B is connected to the gate of the two switching elements M 72 , and the power supply terminal V B is connected to the gate of the two switching elements M 73 through an inverter. The power supply terminals V A and V B provide different voltages to control the switching elements M 71 , the switching elements M 72 , and the switching elements M73 turn-on and turn-off. It should be noted that the electronic elements with the same reference signs in FIG. 1 have the same electrical parameters.

[0064] FIG. 2 shows four turn-on states of the circuit topology shown in FIG. 1. As shown in FIG. 2, if the first filter network and the third filter network are turned off, the second filter network is turned on, and the phase shifter is in a turn-on state a; if the first filter network and the second filter network are turned off, the third filter network is turned on, and the phase shifter is in a turn-on state b; if the first filter network and the second filter network are turned on, the third filter network is turned off, and the phase shifter is in a turn-on state c; if the first filter network and the third filter network are turned on, the second filter network is turned off, and the phase shifter is in a turn-on state d. The four turn-on states of the phase shifter correspond to four insertion phases of the phase shifter, respectively. For example, the turn-on state a corresponds to a reference phase, the turn-on state b corresponds to a first phase, the turn-on state c corresponds to a second phase, and the turn-on state d corresponds to a third phase.

[0065] It should be noted that although the high-pass filter network or the low-pass filter network shown in FIG. 1 is a three-order network, the present application is not limited thereto, and other order (for example, five-order, seven-order, etc.) high-pass filter networks or low-pass filter networks fall within the protection scope of the present application. In addition, although the order of the high-pass filter network and the low-pass filter network shown in FIG. 1 is the same, the present application is not limited thereto, and the order of the first filter network, the second filter network and the third filter network can be the same or different.

[0066] Optionally, in the example of FIG. 2, the first phase is 11.25°, the second phase is 22.5°, and the third phase is 33.75°. The calculation process of the parameters of each capacitor and each inductor in FIG. 1 is described below.

[0067] Firstly, the ABCD matrices of the high-pass filter network and the two low-pass filter networks are named as [A HP ], [A LP1 ] and [A LP2 ], in order to calculate the insertion loss and phase shift of the signal passing through the filter network, it is necessary to first calculate the ABCD matrix of the circuit to solve the transfer function:

[0068] Wherein, the angular frequency ω is set to 2xπx16GHz, C 71 ~ C 73 and L 71 ~ L 73 represent the capacitance value and the inductance value. Since the high-pass filter network and the two low-pass filter networks are connected in parallel, in order to facilitate calculation, the ABCD matrix is converted into Y matrix [Y HP ], [Y LP1 ] and [YLP2

[0069] When the signal only passes through the high-pass filter network, the forward transmission coefficient S21 is:

[0070] where Z is the characteristic impedance, set as 50 Ω, and the corresponding phase shift is:

[0071] When the entire circuit matrix is derived and programmed, in order to realize 11.25°, 22.5° and 33.75° phase shifts, seven constraint equations need to be solved:

[0072] real(X) and imag(X) represent the real part and the imaginary part of the forward transmission coefficient of the signal X, Phase LP1 and Phase LP2 respectively represent the phase of the signal passing through the low-pass filter network I and the low-pass filter network II, and Phase HP is derived from [Y LP1 ], and Phase HP+LP1 represents the phase of the signal passing through the high-pass filter network and the low-pass filter network I at the same time, and the subsequent symbols are similar.

[0073] At this point, the complex circuit calculation is converted into a multi-objective optimization mathematical problem. In order to solve the multi-objective optimization mathematical problem, the embodiment proposes a multi-objective search algorithm based on a particle swarm algorithm for iterative calculation. Figure 3 shows the iterative calculation process, in which the horizontal axis represents the number of iterations, and the vertical axis represents the result error. As shown in Figure 3, after 60 calculations, the result has converged, and finally after 200 iterations, the result error tends to 0, and finally the corresponding capacitance and inductance values of C 71 , C 73 , L 71 and L 73 are obtained. Formulas 1-11 give the corresponding capacitance and inductance values:

[0074] In the embodiment, the iterative optimization process in the circuit design can be simplified by combining intelligent algorithms with circuit design, which provides strong help for solving and analyzing complex circuit networks.

[0075] Unlike most switch compact phase shifters, the switch compact phase shifter proposed in the embodiment has a double-pole three-throw switch, and the three phase shift degrees are integrated in the same circuit topology through the double-pole three-throw switch, breaking the inherent thinking that a switch type phase shift unit can only realize one phase shift degree, so that the corresponding phase shift unit area is reduced by 50%.

[0076] ​Figure 4 is an example circuit topology of an integrated phase shifter according to an embodiment of the present application. As shown in Figure 4, the phase shifter includes, in order from the front input to the rear output, a passive switch type phase shifter, a high / low pass type quadrature signal generation network, a variable gain amplifier based on a Gilbert cell (i.e., the vector modulation module and the logic control module in Figure 4), and a switching switch. The passive switch type phase shifter includes a high / low pass type 180° phase shift unit, a high / low pass type 90° phase shift unit, a switching compact 11.25°, 22.5°, and 33.75° phase shift unit based on a double-pole triple-throw switch (i.e., the switching compact phase shifter in the embodiment of the present application), and an inductance-based bridge T type 45° phase shift unit.

[0077] The variable gain amplifier based on a Gilbert cell refers to an amplifier that achieves variable amplification gain by providing different tail currents for the vector control module in the logic control module to regulate the gain of the transistor. The switching switch includes a first switching element at the output of the high pass type quadrature signal generation network in the high / low pass type quadrature signal generation network and a second switching element at the output of the variable gain amplifier based on a Gilbert cell. When the first switching element is turned on and the second switching element is turned off, the switching switch is switched to be disconnected from the variable gain amplifier, and the integrated phase shifter is a passive switch type phase shifter. When the first switching element is turned off and the second switching element is turned on, the switching switch is switched to be connected to the variable gain amplifier, and the integrated phase shifter is a passive switch and vector synthesis integrated phase shifter. The high / low pass type quadrature signal generation network in the embodiment of the present application will be described below in conjunction with Figure 5a.

[0078] Figure 5a shows an example circuit topology of the high / low pass type quadrature signal generation network in the embodiment of the present application. As shown in Figure 5a, the network includes a low pass filter network composed of one C 91 and two L 91 and a high pass filter network composed of two C 92 and one L 92 . The low pass filter network has two switch elements S1 connected in series at both ends, and the high pass filter network has two switch elements S2 connected in series at both ends. The two switch elements S1 control the conduction and disconnection of the low pass filter network, and the two switch elements S2 control the conduction and disconnection of the high pass filter network. The conduction and disconnection of the switch elements S1 and S2 can be controlled by providing different voltages to the gates of the switch elements S1 and S2 from the power supply terminals V1 and V2. It should be noted that since Figure 5a shows the high / low pass type quadrature signal generation network, both power supply terminals V1 and V2 need to be turned on at the same time to generate two quadrature signals.

[0079] Referring back to FIG. 4, the structure of the high / low pass type 180° phase shift unit in FIG. 4 is similar to the high / low pass type quadrature signal generation network, which is also composed of a high pass filter network, a low pass filter network, and switch components for controlling the on / off states of the high pass filter network and the low pass filter network.

[0080] FIG. 5b shows an example circuit topology of the high / low pass type 180° phase shift unit in the embodiments of the present application. As shown in FIG. 5b, the network includes a five-order high pass filter network composed of three capacitors (two C 41 and one 2C 41 ) and two inductors (L 41 ), and a five-order low pass filter network composed of two inductors (L 42 ) and three capacitors (two C 42 and one 2C 42 ). The five-order low pass filter network is connected in series with switch components M 43 at both ends, the five-order high pass filter network is connected in series with switch components M 41 at both ends, two switch components M 41 control the on / off of the five-order high pass filter network, and two switch components M 43 control the on / off of the five-order low pass filter network.

[0081] In FIG. 5b, the high / low pass type 180° phase shift unit further includes a power supply end V 180° , the power supply end V 180° is connected to the gates of the two switch components M 41 , and the power supply end V 180° is connected to the gates of the two switch components M 43 after passing through an inverter. The power supply end V 180° can control the on / off of the switch components M 41 and M 43 by providing different voltages. It should be noted that other electronic components (such as switch components M 42 and M 44 ) in FIG. 5b are electronic components configured for optimizing the electrical characteristics of the circuit, which are irrelevant to the purpose of the present application and will not be described here.

[0082] The high-pass filter network and the low-pass filter network of the high / low-pass type 180° phase shift unit are both five orders, and only one of the high-pass filter network and the low-pass filter network of the high / low-pass type 180° phase shift unit can be turned on. With the high-pass filter network as a reference phase, the low-pass filter network can generate an insertion phase of 180°. The values of the capacitors and inductors in the high / low-pass type 180° phase shift unit can be calculated and determined by using the "ABCD matrix + particle swarm algorithm" method described above. Referring to FIG. 4, the structure of the high / low-pass type 90° phase shift unit in FIG. 4 is similar to that of the high / low-pass type 180° phase shift unit, and it also consists of a high-pass filter network, a low-pass filter network, and a switch component for controlling the on-off state of the high-pass filter network and the low-pass filter network.

[0083] FIG. 5c shows an example circuit topology of a high / low-pass type 90° phase shift unit in an embodiment of the present application. The circuit structure of the high / low-pass type 90° phase shift unit shown in FIG. 5c is basically the same as that of the high / low-pass type 180° phase shift unit shown in FIG. 5b, and will not be described here. Unlike the high / low-pass type 180° phase shift unit, the high-pass filter network of the high / low-pass type 90° phase shift unit can achieve a phase shift of 90°. With the high-pass filter network as a reference phase, the low-pass filter network can generate an insertion phase of 90°. The values of the capacitors and inductors in the high / low-pass type 90° phase shift unit can be calculated and determined by using the "ABCD matrix + particle swarm algorithm" method described above.

[0084] The compact 11.25°, 22.5°, and 33.75° phase shift units based on the double-pole triple-throw switch in FIG. 4 are the switch compact phase shifters described above in combination with FIG. 1, and will not be described here.

[0085] The inductance-based bridge T type 45° phase shift unit in FIG. 4 can achieve a phase change of 45°.

[0086] The inductance-based bridge T type 45° phase shift unit in an embodiment of the present application will be described below in combination with FIG. 6. As shown in FIG. 6, the phase shift unit includes two inductors L1 in series and a switch element M1 connected in parallel with the branch in which the two inductors L1 are located, and the branch in which the two inductors L1 are located is grounded through a branch in which a switch element M2 is located. In FIG. 6, the voltage applied to the transistors M1 and M2 is V c , and the voltage applied to the transistor M3 is reverse V c (FIG. b uses the symbol When the transistor M1 is off, the transistor M2 is off, and the transistor M3 is on, at this time, the two inductors L1 are in series; the signal is transmitted along the branch where the two inductors L1 are located, and at the same time, the branch where the two inductors L1 are located is grounded through the on transistor M3, thereby forming a "T" type signal transmission structure. When the transistor M1 is on, the transistor M2 is on, and the transistor M3 is off, at this time, the on transistor M1 short-circuits the two inductors L1; the signal is transmitted along the on transistor M1, and at the same time, the signal is grounded through the inductor L2, thereby forming a "T" type signal transmission structure.

[0087] Returning to FIG. 4, the vector modulation module and the logic control module in FIG. 4 are a variable gain amplifier based on a Gilbert cell. FIG. 7 shows a partial enlarged view of the vector modulation module and the logic control module. As shown in FIG. 7, the logic control module includes switch elements S 11 ~S 15 and S 21 ~S 25 , each of the switch elements S 11 ~S 15 and S 21 ~S 25 is connected in series with transistors D 11 ~D 15 and D 21 ~D 25 , respectively. The transistors D 11 ~D 15 and D 21 ~D 25 work in the saturation region to provide tail currents. S 11 ~S 15 and S 21 ~S 25 are selectively turned on to provide multiple tail currents for the vector modulation module. The switch elements S I and S Q between the logic control module and the vector modulation module control the turn-on and turn-off of the logic control module. For example, when the switch elements S I and S Q are turned on, the logic control module can provide tail currents for the vector modulation module; when the switch elements S I and S Q are turned off, the logic control module stops providing tail currents for the vector modulation module. The transistors M8 and M9 in the vector modulation module amplify the I / Q quadrature signals generated by the high / low pass type quadrature signal generating network, and the different tail currents provided by the logic control module for the vector control module control the gain of the transistors M8 and M9, thereby realizing variable gain amplification.

[0088] In FIG. 7, the switch includes a switch element S3 at the output of the high-pass type quadrature signal generation network in the high / low-pass type quadrature signal generation network, and a switch element S4 at the output of the variable gain amplifier based on the Gilbert cell, i.e. the output of the vector modulation module. When S4, S I , S Q are turned on, S3 is turned off, S 11 ~ S 15 and S 21 ~ S 25 are selectively turned on, so that transistors D 11 ~ D 15 and D 21 ~ D 25 work in the saturation region. At this time, the phase shifter works as an integrated passive switch type and vector synthesis type 7-bit phase shifter, and the signal flows through the circuit diagram as shown in FIG. 8. When S3 is turned on, S4, S I , S Q are turned off, S 11 ~ S 15 and S 21 ~ S 25 are turned off, so that transistors D 11 ~ D 15 and D 21 ~ D 25 are turned off. At this time, the logic control module and the vector modulation module stop working, and no longer generate direct current power consumption. The signal directly reaches the output port through the switch S3, and at this time, the phase shifter works as a 5-bit passive switch type phase shifter, and the signal flows through the circuit diagram as shown in FIG. 9.

[0089] In the variable gain amplifier based on the Gilbert cell provided in the embodiments of the present application, the high / low-pass type quadrature signal generation network at the input end only outputs one quadrature signal, thereby simplifying the existing four differential Gilbert cells into two single-ended input Gilbert cells. The input signals at the gates of transistors M8 and M9 are 90° out of phase, and the quadrature signals output from the drains of the two transistors are directly synthesized into three phase shift degrees of 2.8125°, 5.625° and 8.4375°. Not only is the use of the balun avoided, but also the direct current power consumption of the vector modulation module is reduced by 1 / 2 due to the use of only half of the differential Gilbert cell circuit.

[0090] It should be noted that although the circuit topologies shown in FIGS. 4-7 include specific numbers of capacitors, inductors and switch elements, the present application is not limited thereto, and any other circuit topologies that can achieve the same or similar functions are also within the protection scope of the present application. For example, the high-pass filter network and the low-pass filter network in FIG. 5a are of the third order, but high-pass filter networks and low-pass filter networks of other orders (such as fifth order, seventh order, etc.) are also within the protection scope of the present application.

[0091] FIGS. 10-11 show the performance of 7-bit integrated passive switch-type and vector synthesis-type phase shifters in terms of phase shift accuracy, insertion loss and return loss according to embodiments of the present application.

[0092] FIGS. 12-13 show the performance of 5-bit passive switch and vector synthesis integrated phase shifter in terms of phase shift accuracy, insertion loss and return loss according to embodiments of the present application.

[0093] As can be seen from FIGS. 10-13, the phase shifter according to embodiments of the present application exhibits excellent performance in terms of phase shift accuracy, insertion loss and return loss.

[0094] Compared with the prior art, the embodiments of the present application can achieve at least one of the following beneficial effects:

[0095] 1. The present application innovatively proposes a compact switch-type phase shift unit based on a double-pole triple-throw switch (DPTTS), which integrates multiple phase shift units in the same circuit topology through the DPTTS, so that the area of the corresponding phase shift unit is greatly reduced, thereby meeting the demand for miniaturization and low cost of the phase shifter.

[0096] 2. The present application integrates a passive switch-type phase shifter and a vector synthesis-type phase shifter. The passive switch-type phase shifter has low phase shift accuracy, but has no DC power consumption in ideal conditions. When the phase shift accuracy requirement is high, the vector synthesis-type phase shifter is switched, and when the phase shift accuracy requirement is low, the passive phase shifter is switched to reduce power consumption.

[0097] 3. The phase shifter according to the present application exhibits excellent performance in terms of phase shift accuracy, insertion loss and return loss.

[0098] The above description is only a preferred embodiment of the present application, but the protection scope of the present application is not limited thereto. Any changes or replacements within the technical scope disclosed by the present application can be easily thought of by those skilled in the art, and should be covered within the protection scope of the present application.

Claims

1. A compact switching phase shifter, characterized in that, include: The first filtering network is an Nth-order high-pass filtering network. The second filtering network is an M-order low-pass filtering network. The third filtering network is an R-order low-pass filter network. The first filter network, the second filter network, and the third filter network are connected in parallel via a double-pole triple-throw switch. When the second filter network is turned on alone, the insertion phase of the switch compact phase shifter is the reference phase; When the third filter network is turned on alone, the insertion phase of the switch compact phase shifter is the first phase; When the first filter network and the second filter network are individually turned on, the insertion phase of the switch compact phase shifter is the second phase; When the first filter network and the third filter network are individually turned on, the insertion phase of the switch compact phase shifter is the third phase.

2. The compact phase shifter according to claim 1, characterized in that, The double-pole triple-throw switch includes: A first switching unit connected in series with the first filtering network controls the on and off states of the first filtering network. A second switching unit connected in series with the second filter network controls the on and off states of the second filter network; A third switching unit connected in series with the third filter network, the third switching unit controlling the on and off of the third filter network; The first power supply terminal is connected to the first switching unit. The second power supply terminal is connected to the second switching unit, and the... The second power supply terminal is connected to the third switching unit after passing through an inverter; wherein The first power supply terminal controls the on and off of the first switching unit, and the second power supply terminal controls the on and off of the second switching unit and the third unit.

3. The compact phase shifter according to claim 2, characterized in that, The first switching unit includes two first transistors, which are located at the input and output terminals of the first filter network, respectively; the second switching unit includes two second transistors, which are located at the input and output terminals of the second filter network, respectively; the third switching unit includes two third transistors, which are located at the input and output terminals of the third filter network, respectively.

4. The compact switching phase shifter according to any one of claims 1 to 3, characterized in that, N, M, and R are all equal to 3, and the first phase is 11.25°, the second phase is 22.5°, and the third phase is 33.75°.

5. The compact phase shifter according to claim 1, characterized in that, The inductance and capacitance parameters in the aforementioned compact phase shifter are determined by the following method: Based on the first phase, the second phase, and the third phase, establish constraint equations for solving the inductance and capacitance parameters; and A multi-objective search algorithm based on particle swarm optimization is used for iterative calculation to solve the constraint equations until the results converge.

6. An integrated phase shifter, characterized in that, include: Passive switch-type phase shifter, quadrature signal generation network, variable gain amplifier, switching switch; among them... The passive switch-type phase shifter, the quadrature signal generation network, and the variable gain amplifier are cascaded in sequence. The passive switching phase shifter includes the switching compact phase shifter according to any one of claims 1 to 5; and When the switching switch is switched to disconnect from the variable gain amplifier, the integrated phase shifter is a passive switching phase shifter; When the switching switch is switched to establish a connection with the variable gain amplifier, the integrated phase shifter is a passive switch and vector synthesis integrated phase shifter.

7. The integrated phase shifter according to claim 6, characterized in that, The switching switch is cascaded at the output of the variable gain amplifier. The switching switch includes a first switch and a second switch. When the first switch is on and the second switch is off, the variable gain amplifier is in operation. The integrated phase shifter is a passive switch and vector synthesis integrated phase shifter. When the first switch is off and the second switch is on, the variable gain amplifier stops working. The integrated phase shifter is a passive switch type phase shifter.

8. The integrated phase shifter according to claim 6, characterized in that, The variable gain amplifier is a variable gain amplifier based on Gilbert units.

9. The integrated phase shifter according to claim 6, characterized in that, The passive switching type phase shifter also includes: A first high-pass / low-pass phase shifting unit, a second high-pass / low-pass phase shifting unit, and a bridge T-type phase shifter based on capacitance or inductance; wherein... The first high-pass phase shifter, the second high-pass phase shifter, the switch-compact phase shifter, and the bridge T-type phase shifter based on capacitance or inductance are cascaded in sequence.

10. The integrated phase shifter according to claim 9, characterized in that, The first high-pass / low-pass phase shifter generates a 180° phase change, the second high-pass / low-pass phase shifter generates a 90° phase change, the switch compact phase shifter generates phase changes of 11.25°, 22.5°, and 33.75°, the capacitor-based or inductor-based bridge T-type phase shifter generates a 45° phase change, and the variable gain amplifier generates a phase change of 0–8.4375° in steps of 2.8125°.

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