An ultra-wideband detection and jamming integrated antenna-feeder system

Abstract

The present application relates to the field of integrated antenna, in particular to a kind of ultra-wideband reconnaissance jamming school integrated antenna feed system.It contains omnidirectional monitoring antenna, four azimuth plane transmitting antenna array and direction-finding antenna array covering 360 ° azimuth, positioning module, gyroscope, calibration module, digital processing module, instantaneous frequency measurement receiver, general monitoring receiver, direction-finding receiver and T component;Omnidirectional monitoring antenna is used to monitor and receive 360 ° azimuth electromagnetic signal;Four azimuth plane transmitting antenna array is connected with T component, and according to the direction-finding azimuth, the signal set is interfered, and four azimuth plane direction-finding antenna array is composed of 4 pairs of antennas, and is used for interferometer direction-finding to the signal set;Positioning module is used to receive positioning signal, and provides positioning information and time reference for system;Gyroscope is used for self-positioning to system attitude, and provides the angle deflection angle information of equipment relative to north for system.The present application is suitable for electronic countermeasure system.

Description

TECHNICAL FIELD

[0001] The present application relates to the field of integrated antennas, in particular to an ultra-wideband detection-jamming-calibration integrated antenna feeder system. BACKGROUND

[0002] The current antenna feeder system in the field of electronic countermeasures has significant bottlenecks in ultra-wideband coverage, multi-functional integration, and dynamic environment adaptability, mainly embodied in:

[0003] 1. Frequency band coverage and hardware separation problem

[0004] Narrowband segmented design:

[0005] Existing systems mostly use independent hardware to cover different frequency bands (such as S / C / X band separate antennas), resulting in the need for multiple devices to cooperate for 1-40GHz ultra-wideband coverage, which is bulky.

[0006] 2. Efficiency defects caused by functional separation

[0007] Detection, jamming, and calibration modules are isolated:

[0008] Calibration needs to interrupt the jamming process, with poor real-time performance (switching time > 100ms); separate design of jamming sources and calibration sources increases hardware cost by more than 30%.

[0009] Resources are not reused: the direction finding channel is only used for positioning, and the transmit array is only used for jamming, with fixed functions.

[0010] 3. Dynamic scene precision misalignment

[0011] Attitude compensation is missing: the pitch / roll motion of the mobile platform causes the beam to deviate, and the error of the traditional static direction finding algorithm is ≥1°;

[0012] Environmentally sensitive: receivers are easily saturated under strong signals (especially in self-jamming scenarios), and the insertion loss of existing amplifiers fluctuates by >3dB in wide frequency bands. SUMMARY

[0013] The purpose of the present application is to overcome the shortcomings of the prior art and provide an ultra-wideband detection-jamming-calibration integrated antenna feeder system that can simultaneously complete signal monitoring, accurate direction finding, directional jamming, and real-time self-calibration functions, solving the defects of traditional separate devices in wide frequency coverage, dynamic precision, and system efficiency.

[0014] The present application achieves the above-mentioned purpose by adopting the following technical solutions: the present application provides an ultra-wideband detection-jamming-calibration integrated antenna feeder system, comprising:

[0015] It comprises: an omnidirectional monitoring antenna, four azimuth plane transmitting antenna arrays and direction-finding antenna arrays covering 360° azimuth, a positioning module, a gyroscope, a calibration module, a digital processing module, an instantaneous frequency measurement receiver, a general monitoring receiver, a direction-finding receiver and a T component;

[0016] The omnidirectional monitoring antenna is connected with the instantaneous frequency measurement receiver and the general monitoring receiver respectively, and is used for monitoring and receiving electromagnetic signals in 360° azimuth.

[0017] The four azimuth plane transmitting antenna arrays are distributed at intervals of 90° and are connected with the T component, and are used for interfering with the set signals according to the direction-finding azimuth, and the four azimuth plane direction-finding antenna arrays are each composed of four pairs of antennas and are used for interferometer direction-finding of the set signals.

[0018] The positioning module is used for receiving positioning signals and providing positioning information and time reference for the system.

[0019] The gyroscope is used for self-positioning of the system attitude and providing the angle deviation information of the device relative to the true north for the system.

[0020] The direction-finding receiver is composed of a calibration source module, a frequency source module and four phase-coherent frequency conversion receiving modules, is used for interferometer direction-finding of the signals received by the direction-finding antenna arrays, and gives the direction of the set signals, the calibration source module simultaneously inputs the signal source for the T component to form the interference signals on the required frequency, and the frequency source module provides multiple frequency sources for the direction-finding receiver, the general monitoring receiver and the calibration module, including fixed frequency and variable frequency sources.

[0021] The general monitoring receiver monitors the signals output by the omnidirectional monitoring antenna, measures the signal frequency, bandwidth and pulse parameters after finding the set signals.

[0022] The digital processing module is connected with the instantaneous frequency measurement receiver, the general monitoring receiver and the direction-finding receiver respectively, and is used for processing the intermediate frequency signals.

[0023] Further, the T component comprises an SPST (Single Pole Single Throw), a push amplifier, a power divider, a phase shifter, an attenuator, a push amplifier, a power amplifier and an isolator, the input is input into the push amplifier after passing through the SPST, the push amplifier outputs to the power divider, the power divider divides the output signals into multiple output signals with equal amplitude and equal phase, and each output signal is sequentially output after passing through the phase shifter, the attenuator, the push amplifier, the power amplifier and the isolator.

[0024] Further, the system further comprises an active front end, which is installed close to the antenna, and the active front end comprises a limiter, a filter, a first SPDT (Single Pole Double Throw) switch, a second SPDT switch, a low noise amplifier, and an attenuator, the input signal is sequentially output after passing through the limiter, the filter, the first SPDT switch, the low noise amplifier, the second SPDT switch, and the attenuator, and the first SPDT switch and the second SPDT switch are straight through.

[0025] Further, the system further comprises a signal switching module, which is used for switching and selecting the signals of the four azimuth planes of the transmitting antenna array and the direction finding antenna array and outputting to the T component or the direction finding receiver, and the signal switching module comprises 4 SP4T switches, which are used for switching the direction finding antennas of the four azimuth planes; and 16 SP4T switches, which are used for selecting the transmitting phased array antennas of the four azimuth planes.

[0026] Further, the coherent frequency conversion receiving module comprises a limiter, a SPDT, a first digital control attenuator, a first switch filter group, a low noise amplifier, a first mixer, a second switch filter group, a second digital control attenuator, a first amplifier, a second mixer, a second amplifier, a third digital control attenuator, a digital control phase shifter, a third amplifier, and a third switch filter group, the calibration input is connected through the SPDT, the radio frequency input passes through the limiter, the SPDT, the first digital control attenuator, the first switch filter group, and the low noise amplifier to reach the first mixer, the second local oscillator input is input into the first mixer, and after being processed by the first mixer, the signal sequentially passes through the second switch filter group, the second digital control attenuator, and the first amplifier to reach the second mixer, the first local oscillator input is input into the second mixer, and after being processed by the second mixer, the signal sequentially passes through the second amplifier, the third digital control attenuator, the digital control phase shifter, the third amplifier, and the third switch filter group, and after being processed by the third switch filter group, the signal is output.

[0027] Further, the general monitoring receiver adopts the same architecture as the coherent frequency conversion receiving module, which comprises a limiter, a first digital control attenuator, a first switch filter group, a low noise amplifier, a first mixer, a second switch filter group, a second digital control attenuator, a first amplifier, a second mixer, a second amplifier, a third digital control attenuator, a digital control phase shifter, a third amplifier, and a third switch filter group, the radio frequency input passes through the limiter, the first digital control attenuator, the first switch filter group, and the low noise amplifier to reach the first mixer, the second local oscillator input is input into the first mixer, and after being processed by the first mixer, the signal sequentially passes through the second switch filter group, the second digital control attenuator, and the first amplifier to reach the second mixer, the first local oscillator input is input into the second mixer, and after being processed by the second mixer, the signal sequentially passes through the second amplifier, the third digital control attenuator, the digital control phase shifter, the third amplifier, and the third switch filter group, and after being processed by the third switch filter group, the signal is output.

[0028] Further, the calibration module adopts the same architecture as the phase coherent frequency conversion receiving module, comprising a first digital control attenuator, a first switch filter group, a low noise amplifier, a first mixer, a second switch filter group, a second digital control attenuator, a first amplifier, a second mixer, a second amplifier, a third digital control attenuator, a digital control phase shifter, a third amplifier and a third switch filter group, the intermediate frequency signal is sequentially processed by the third switch filter group, the third amplifier, the digital control phase shifter, the third digital control attenuator and the second amplifier, and then reaches the second mixer, the first local oscillator is input into the second mixer, and after being processed by the second mixer, the signal is sequentially processed by the first amplifier, the second digital control attenuator and the second switch filter group, and then reaches the first mixer, the second local oscillator is input into the first mixer, and after being processed by the first mixer, the signal is sequentially processed by the low noise amplifier, the first switch filter group and the first digital control attenuator, and then output.

[0029] The present application has the following advantages:

[0030] The present application synchronously realizes the functions of electromagnetic signal detection, directional interference and real-time calibration through hardware cooperation and dynamic closed-loop control, contains an omnidirectional detection antenna, a multi-band cooperative array, a reconfigurable radio frequency front end and a closed-loop calibration unit, and can synchronously complete signal monitoring, accurate direction finding, directional interference and real-time self-calibration functions in the frequency band of 1-18GHz, and solve the defects of traditional discrete devices in wide frequency coverage, dynamic precision and system efficiency. BRIEF DESCRIPTION OF DRAWINGS

[0031] Figure 1 is a super wide frequency band detection and interference integrated antenna system structure block diagram provided by the present application;

[0032] Figure 2 is a T component structure block diagram provided by the present application;

[0033] Figure 3 is an active front end structure block diagram provided by the present application;

[0034] Figure 4 and Figure 5 is a signal switching module structure schematic diagram provided by the present application;

[0035] Figure 6 is a phase coherent frequency conversion receiving module structure block diagram in a direction finding receiver provided by the present application;

[0036] Figure 7 is a general receiver structure block diagram provided by the present application;

[0037] Figure 8 is a calibration source module structure block diagram provided by the present application;

[0038] Figure 9It is the frequency source module structure schematic diagram provided by the present application;

[0039] Figure 10 It is the 100M clock output provided by the present application;

[0040] Figure 11 It is the 31-39G local oscillator source structure block diagram provided by the present application;

[0041] Figure 12 It is the 17.25G and 23.75G local oscillator source structure block diagram provided by the present application. DETAILED DESCRIPTION

[0042] In order to make the purpose, technical scheme and advantages of the embodiments of the present application more clear, the technical scheme in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application.

[0043] The present application provides a kind of ultra-wideband frequency detection and interference integrated antenna system, as shown in Figure 1 It includes: omnidirectional monitoring antenna, four azimuth plane transmitting antenna array and direction finding antenna array covering 360 ° azimuth, positioning module, gyroscope, calibration module, digital processing module, instantaneous frequency measurement receiver, general monitoring receiver, direction finding receiver and T component;

[0044] The omnidirectional monitoring antenna is connected with the instantaneous frequency measurement receiver and the general monitoring receiver respectively, and the 1-18GHz omnidirectional monitoring antenna is used for monitoring and receiving electromagnetic signals in 360 ° azimuth;

[0045] The four azimuth plane transmitting antenna array is distributed at an interval of 90 °, and is connected with the T component, and interferes with the set signal according to the direction finding azimuth, and the four azimuth plane direction finding antenna array is composed of 4 pairs of antennas, and is used for interferometer direction finding of the set signal, and the set signal refers to the frequency signal in 1-18GHz;

[0046] The positioning module is used for receiving positioning signals, and provides positioning information and time reference for the system;

[0047] The gyroscope is used for self-positioning of system attitude, and provides the angle deviation information of the device relative to the north for the system;

[0048] The direction finding receiver is composed of a calibration source module, a frequency source module and four phase-related frequency conversion receiving modules, and performs interferometer direction finding on the signals received by the direction finding antenna array, and gives the direction of the set signal, the calibration source module simultaneously inputs the signal source for the T component, and forms the interference signal on the required frequency, and the frequency source module provides multiple frequency sources for the direction finding receiver, the general monitoring receiver and the calibration module, including fixed frequency and variable frequency source;

[0049] The general monitoring receiver monitors the signal output by the omnidirectional monitoring antenna, and measures the signal frequency, bandwidth and pulse parameters after finding the set signal.

[0050] The digital processing module is composed of 4-way coherent A / D, 2-way non-coherent A / D, 1-way D / A, FPGA (Field-Programmable Gate Array) + DSP (Digital Signal Processor) + Arm, which realizes synchronous sampling, DDC, filtering, FFT, phase measurement and direction finding output of 4-way intermediate frequency signals, frequency sweep monitoring of 1-way general receiver, sampling, DDC, filtering and FFT of intermediate frequency signals, output of spectrum and parameter measurement, and digital / analog conversion of digital signals by 1-way D / A according to needs to generate baseband calibration signals or interference signals. The digital processing board also realizes the functions of required control, communication interface, data exchange with the host computer and the like.

[0051] The motherboard provides RF interfaces (including intermediate frequency, LO1, LO2A, LO2B, calibration) and control interfaces (including power supply and control signals) for the direction finding frequency conversion receiving module, frequency source module, calibration / interference source module and the like, and realizes functions of power division, control switching and the like of local oscillator signals and calibration signals. A separate control board or a digital processing board can also be installed.

[0052] As shown in Figure 2 Fig. 1, which is a schematic structural block diagram of a T component, the T component includes an SPST, a push-pull amplifier, a power divider, a phase shifter, an attenuator, a push-pull amplifier, a power amplifier and an isolator. The input signal passes through the SPST and then enters the push-pull amplifier. The push-pull amplifier outputs to the power divider. The power divider divides the output signal into multiple output signals with equal amplitude and equal phase. Each output signal is sequentially output after passing through the phase shifter, the attenuator, the push-pull amplifier, the power amplifier and the isolator.

[0053] The SPST switch is used to turn on or turn off the input signal, and has a high isolation requirement. The attenuator is used to compensate for the amplitude inconsistency of each output path, and the control range is 0-8 dB, and the control accuracy is better than 0.4 dB. The power divider divides one output signal into 16 paths with equal amplitude and equal phase, and has a high consistency requirement. The phase shifter is used for beam pointing control, and needs to compensate for the phase inconsistency of each path at the working frequency in the pointing control. The push-pull amplifier and the power amplifier push the signal to the required transmission power, and need to select a device with good linearity, and preferably a push-pull power amplifier device. The isolator is used to adapt the reverse isolation of the signal, absorb the reflected power, and protect the power amplifier.

[0054] As shown in Figure 3As shown, it is an active front-end structure diagram, the active front-end includes a limiter, a filter, a first SPDT switch, a second SPDT switch, a low noise amplifier and an attenuator, the input signal is sequentially output after passing through the limiter, the filter, the first SPDT switch, the low noise amplifier, the second SPDT switch and the attenuator, and the first SPDT switch and the second SPDT switch are straight-through.

[0055] The active front-end is installed close to the antenna, and mainly functions to improve the antenna induced signal power, facilitate channel detection and signal processing. The main device of the front-end is a low noise amplifier, a high linearity device with a small noise coefficient is selected to improve the system noise coefficient of the receiving system and improve the detection sensitivity. In order to protect the system and improve the anti-power attack performance, a limiter is added at the input end to suppress excessively high power input to the low noise amplifier. For an especially strong input signal, the low noise amplifier will be saturated or serious nonlinear distortion will be generated after passing through the low noise amplifier, and therefore a straight-through bypass of the low noise amplifier is designed.

[0056] As shown in Figure 4 and Figure 5 As shown, it is a signal switching module structure diagram, which is used for selecting the direction finding array surface and the transmitting array surface respectively. The signal switching module is used for switching and selecting the signals of the four azimuth surface transmitting antenna arrays and the direction finding antenna arrays, and outputting to the T components or the direction finding receivers. The signal switching module includes four SP4T switches used for switching the four azimuth surface direction finding antennas, and sixteen SP4T switches used for selecting the four azimuth surface transmitting phased array antennas.

[0057] Figure 4 In the figure, A1-A4, B1-B4, C1-C4 and D1-D4 are respectively the front-ends of the direction finding antenna array A surface, P1-P4 represent the input ends of the direction finding receivers 1-4, Figure 5 In the figure, TA1-TA16, TB1-TB16, TC1-TC16 and TD1-TD16 are respectively the array surface antennas of the transmitting antenna array, and PT1-PT16 represent the output ends of the T components 1-16.

[0058] As shown in Figure 6As shown, it is a principle structure block diagram of the phase-locked frequency conversion receiving module. The phase-locked frequency conversion receiving module comprises a limiter, a SPDT, a first digital attenuator, a first switch filter group, a low noise amplifier, a first mixer, a second switch filter group, a second digital attenuator, a first amplifier, a second mixer, a second amplifier, a third digital attenuator, a digital phase shifter, a third amplifier, and a third switch filter group. The calibration input is connected through the SPDT switch, the radio frequency input is connected through the limiter, the SPDT, the first digital attenuator, the first switch filter group, and the low noise amplifier to the first mixer, the second local oscillator input is connected to the first mixer, and after the first mixer processing, the signal is sequentially connected to the second switch filter group, the second digital attenuator, and the first amplifier to the second mixer, the first local oscillator input is connected to the second mixer, and after the second mixer processing, the signal is sequentially connected to the second amplifier, the third digital attenuator, the digital phase shifter, the third amplifier, and the third switch filter group, and after the third switch filter group processing, the signal is output.

[0059] The first switch filter group, the second switch filter group, and the third switch filter group all adopt the combination of a band pass filter and a SPDT switch.

[0060] Considering that the bandwidth of the input signal covers two frequency multiplication ranges, if once down conversion is adopted, the local oscillator output range is 9.75-21.75G, and the following difficulties will be caused:

[0061] The image frequency falls near the intermediate frequency;

[0062] The local oscillator frequency is easily mixed with the intermediate frequency;

[0063] The filter design is difficult, the harmonic and local oscillator signals cannot be filtered out, and the spurious suppression is also difficult.

[0064] Therefore, the twice frequency conversion + channel segmentation scheme needs to be considered.

[0065] The radio frequency antennas are relatively close, so the receiving channel may be interfered by strong interference when transmitting, and therefore a 4W continuous wave limiter is added. The limiting power is 17dBm, at this time, the two-stage amplifier is pushed to saturation, and when the system transmits, all the digital attenuators can be opened to attenuate the high power, so as to prevent the link from being abnormal, the maximum input power of the switch is 1W, and the anti-burning capacity after limiting is provided. At the same time, the maximum input power of the chip and the saturation output power of the chip after limiting determine that the LNA chip and the mixer have a certain anti-burning capacity.

[0066] In order to reduce the noise figure, the band pass filter is designed in front of the mirror to suppress the image. Since the design divides 1-18GHz into two segments, and the sweep is also time-division, the corresponding system first intermediate frequency (corresponding to the RF of the mixer) is also designed into two points, 21GHz and 27.5GHz. The first local oscillator is also designed into two, one for 31-39GHz, and the corresponding intermediate frequency frequency band of the mixer is 10-18GHz. One is for the intermediate frequency frequency band of the mixer, which is 1-11GHz. The local oscillator frequency is set to 31-36GHz. The relative bandwidth of the two wideband filters is less than 60%, which is convenient to realize. The local oscillator of the second mixer is set to 17.25 and 23.75. Mainly to stagger with the first intermediate frequency of 21 and 27.5. Make the local oscillator and the first intermediate frequency mixing spurs can be fully suppressed. Finally, through the second mixing, 21G and 27.5G are down-converted to 3.75G. In the 3.75G intermediate frequency, the temperature compensation and phase adjustment and power adjustment are carried out to adjust the linearity between stages.

[0067] As shown in Figure 7 The channel module and the direction finding frequency conversion module of the general monitoring receiver do not have the input of the calibration signal compared with the direction finding frequency conversion module. Therefore, an SPDT switch in the front end is not needed, which reduces the noise figure and improves the flatness in the band. Another influence is that the power input at each stage may be affected, especially the power of the first stage. However, since the input is still less than the maximum input power of the low noise amplifier, the attenuator can also be opened for protection.

[0068] Specifically, the general monitoring receiver adopts the same architecture as the coherent frequency conversion receiving module, including an amplitude limiter, a first digital controlled attenuator, a first switch filter group, a low noise amplifier, a first mixer, a second switch filter group, a second digital controlled attenuator, a first amplifier, a second mixer, a second amplifier, a third digital controlled attenuator, a digital controlled phase shifter, a third amplifier, and a third switch filter group. The radio frequency input passes through the amplitude limiter, the first digital controlled attenuator, the first switch filter group, and the low noise amplifier to reach the first mixer. The second local oscillator input the first mixer, and after being processed by the first mixer, passes through the second switch filter group, the second digital controlled attenuator, and the first amplifier to reach the second mixer. The first local oscillator input the second mixer, and after being processed by the second mixer, passes through the second amplifier, the third digital controlled attenuator, the digital controlled phase shifter, the third amplifier, and the third switch filter group. After being processed by the third switch filter group, it is output.

[0069] As shown in Figure 8The diagram shows the structure of the calibration module. The calibration module sends the 3.75GHz intermediate frequency (IF) signal from the digital output to the calibration channel or transmits it through an antenna. The scheme uses the same frequency source and architecture as the direction-finding frequency conversion channel for frequency conversion. This allows the use of some of the same components. The difference lies in the IF output power, which is -20 to 0 dBm. The output is 10 dBm when it is an interference signal and -30 dBm when it is a calibration signal. Therefore, the channel gain requirement is low, with a maximum of 30 dBm. The channel power control requirement is high, requiring 40 dB. Additionally, a 31 dB power control requirement is needed, with 1 dB increments. Considering that using a 31.5 dB digitally controlled attenuator for power control might not actually provide a 31 dB control range, the 40 dB power control is split into two 31.5 dB digitally controlled attenuators. The mixer output is amplified after filtering out the IF signal and the local oscillator.

[0070] When the output is set to interference, the attenuation of the digitally controlled attenuator decreases; when the output is set to calibration, the attenuation of the digitally controlled attenuator increases.

[0071] like Figure 9 The diagram shows the structure of the frequency source module. LO1, LO1A, and LO1B represent three independent variable frequencies of 31-39 GHz, and LO2, LO2A, and LO2B represent three independent fixed frequencies of 17.25 / 23.75 GHz. Figure 9 In CTL, it stands for Control.

[0072] Figure 10 For the 100MHz clock output, the 100MHz reference input passes through a temperature-compensated crystal oscillator and a low-pass filter before entering a 2-to-1 power divider, splitting into two paths. Each path then passes through an attenuator and an amplifier before being output to a 3-to-1 power divider, resulting in three paths for amplitude and phase adjustment. To ensure spurious and phase noise control, a custom clock module is selected for the 100MHz clock, which is back-engineered according to 10GHz phase noise requirements with a certain margin added.

[0073] Figure 11 The local oscillator structure is for 31~39GHz. The reference input passes through a phase-locked loop, a voltage-controlled oscillator, an amplifier, a passive frequency multiplier, a bandpass filter, and an equalizer in sequence before being output to power divider 1-2, which splits it into two paths. Each path is then amplified and output to power divider 1-3, which splits it into three output paths.

[0074] Figure 12 The structure is a 17.25 / 23.75GHz local oscillator. The two reference inputs are output to the SPDT switch after passing through a phase-locked loop, a voltage-controlled oscillator, and a low-pass filter, respectively. After the SPDT switch, a fixed attenuator, a low-noise amplifier, a low-pass filter, and a power divider are connected. The power divider splits the signal into two outputs, and each output is then split into three outputs by another power divider.

[0075] Because the antenna input of instantaneous frequency measurement can be interfered by the transmitter, an input increase limiter is added to prevent the first stage power amplifier intermodulation from falling into the frequency measurement range due to out-of-band spurs. Therefore, a wideband filter is added before the first stage amplifier, and the input power of the limiter is still 17 dBm. Therefore, a 1-bit digital attenuator is reserved before the first stage amplifier. When the input power is large, the digital attenuator of the front stage needs to be turned on. Therefore, a wideband coupler is used to couple the power for power detection, and the detection voltage is sent to the MCU, and the attenuation value range is determined by the MCU.

[0076] In order to ensure the time of instantaneous frequency measurement, the input signal is divided into 6 sub-bands. 3 power dividers are used.

[0077] Phased array antenna unit design (transmit antenna array and direction finding antenna array):

[0078] Limited by the working frequency, bandwidth, polarization mode and the beam width of the elevation plane, the antenna unit needs to meet the following conditions: in the frequency band of 1-18 GHz, under the condition of 45° oblique polarization, the beam of the elevation plane covers 5-85°, the antenna gain is adapted to the frequency, the port is well matched, and the structure of the reflecting surface has little effect on the beam characteristics. According to these restrictive conditions, the Vivalid form is first selected for the antenna unit, which is convenient for processing, easy to feed, and has good bandwidth characteristics. Restricted by the highest working frequency and the beam scanning range, the maximum interval of the array is limited to 9.5 mm, the azimuth beam width is not less than 6°, the array gain is as high as possible, and the feeding is convenient. A 1x16 one-dimensional uniform linear array is adopted. The specific design is as follows.

[0079] Transmit antenna array design:

[0080] The working frequency band of the transmit antenna array is 1-18 GHz, which belongs to a super wideband antenna. Generally, log-periodic antennas, Vivaldi antennas and other elements are used to form an array. The log-periodic antenna form is used in this frequency band, which is difficult to feed and has poor consistency; the Vivaldi antenna form has a beam width of only 30-50° in the high frequency band, which does not meet the requirement of 70° instantaneous coverage of the array in the elevation direction. At the same time, the longitudinal size of these two kinds of antennas is large, and the gain attenuation is large when the scanning angle is large.

[0081] The working bandwidth of the transmit array spans three times the frequency, and the minimum element spacing should be less than 0.58λmin to meet the ±45° scanning range, and the structure is compact, and the coupling between elements is serious.

[0082] This array adopts super wideband dipole antenna design technology, and the performance of a single element is optimized to VSWR≤2.5 and in-band gain 0-5dBi through optimization of the structure parameters of the meandered dipole and coupling loading measures.

[0083] After the array is formed, the inter-element distance is small, the array is compact, the in-array coupling effect is basic, and the VSWR of each antenna feed port in the array is less than 3.0 by adjusting the structure parameters of the antenna. The array gain is affected by the effective area of the array and the efficiency of the feed network. The T component of the array is pre-posed, close to the antenna port, and the loss mainly comes from the 0.4 dB insertion loss of the isolator.

[0084] The transmitting array requires 45° oblique polarization. After the broadband dipole antenna is arranged in a 45° inclined structure, due to the compact structure, the coupling effect is serious. When the array is scanned to -45° and +45°, the beam of the array at the high frequency changes in the pointing direction of the elevation plane and cannot maintain the constant normal direction.

[0085] Polarization twist

[0086] The array adopts a vertical polarization array structure and realizes polarization rotation through a polarization grid to meet the requirement of 45° oblique polarization.

[0087] Design of the direction-finding antenna array:

[0088] The main function of the direction-finding receiving channel is to change the spatial electromagnetic signals perceived by the antenna array into intermediate frequency signals convenient for signal collection and processing through filtering, amplification, and mixing. In order to accurately reflect the electromagnetic characteristics of the signals perceived by the array, the consistency of the receiving channel is required to be high. For the amplitude consistency control, the amplitude-frequency characteristics of the components at each stage of the receiving channel link are required to be consistent, and the incoherence deviation is adjusted through the attenuator to ensure that the amplitude inconsistency between the channels meets the error tolerance requirement. For the phase inconsistency control of the receiving channel, on the one hand, the local oscillator signals are required to be homologous or in phase to ensure the stability of the phase difference between the receiving channels; on the other hand, the phase-frequency characteristics of the components at each stage are required to be consistent, the phase delay of the signal transmission link is required to be consistent, the incoherence is compensated, and the phase inconsistency between the channels is ensured to meet the error tolerance requirement.

[0089] Suppression of second harmonic

[0090] The RF input range of the receiving channel is 1~18 GHz. After the low frequency signals are amplified by the input low noise amplifier, the second harmonic is still within the input signal range. In order to suppress the in-band second harmonic, the signal is first passed through a preselector after input, and then enters the mixing process. The frequency band of the preselector is divided into 1~11 GHz and 10~18 GHz. The filter is 1 GHz outside the passband, and the suppression degree is greater than 40 dBc.

[0091] In order to improve the direction-finding sensitivity, the bandwidth of the intermediate frequency of the receiving channel is set to two grades of 2 GHz / 500 MHz.

[0092] System error calibration:

[0093] This antenna subsystem is used for direction finding and beam forming, and has high requirements for phase accuracy. In the 1-18 GHz frequency band, on the one hand, consistency control is strengthened from the design and processing technology to ensure that the consistency index of the system is as good as possible, and on the other hand, system error calibration work also needs to be carried out to measure the inherent error of the phase consistency requirement of the system as the error calibration basis for the direction finding algorithm or the phase shift control correction of the phased array.

[0094] Error control of the direction finding antenna array

[0095] The direction finding antenna unit adopts the PCB manufacturing process, and its processing accuracy is high. The main source of error is the control of the installation accuracy of the output port socket. The installation accuracy is controlled according to an error of 3°:

[0096]

[0097]

[0098] In the formula, indicates the antenna position error, indicates the phase error, indicates the antenna wavelength, indicates a constant unit related to the signal incident angle.

[0099] Therefore, when installing the socket, the installation error needs to be controlled to be less than 0.1 mm.

[0100] Another important source of error of the direction finding system is the active front end and the receiving channel, which is a system error and can be measured. Through measurement, the phase from each side of the direction finding antenna output port to the corresponding selected output port can be tested to form error data. After the phase difference participating in direction finding is corrected, DOA estimation is performed, and the antenna feeder subsystem provides error data samples for measurement.

[0101] Error control of the transmitting phased array:

[0102] The beam pointing accuracy of the phased array is affected by the consistency of each array element and the phase shift accuracy. In order to improve the beam control quality, the phase from the input end of the T component to each array antenna port needs to be tested to form phase error data that changes with frequency.

[0103] When performing phase control, the phase shift error correction is performed:

[0104] The array element spacing of the phased array is (mm), and if the system phase error of the 5th path of the transmitting array at a frequency of (GHz) is (°), and the expected pointing direction of the beam control is , then the theoretical phase of the phase shift is:

[0105]

[0106] Phase shifter phase shift amount:

[0107] Control phase shifter, actual phase shift value ([ ] indicates rounding).

[0108] The above description is merely that of the preferred embodiments of the application, and it is understood that the application is not limited to that particular form, but is amenable to variations in the above teachings with the intention being that the application be used only insofar as the broadest teachings and the patentable novelty are concerned. Changes in other parameters should be understood as being intended. Changes are both to the substance of the application and to the procedures for its performance are intended to be covered therein. The application being put into practice in the fashion set forth or adaptations thereof, as further modification are intended to be within the scope of the application. It is therefore desired to be secured a patent upon all adaptations and modifications falling within the scope of the application.

Claims

1. An ultra-wideband detection and jamming integrated antenna-feeder system, characterized in that, Comprise: Omnidirectional monitoring antenna, four azimuth plane transmitting antenna array and direction-finding antenna array covering 360° azimuth, positioning module, gyroscope, calibration source module, digital processing module, instantaneous frequency measurement receiver, general monitoring receiver, direction-finding receiver and T component; Omnidirectional monitoring antenna is connected with instantaneous frequency measurement receiver and general monitoring receiver respectively, and is used for monitoring and receiving electromagnetic signals in 360° azimuth; Four azimuth plane transmitting antenna array is distributed at intervals of 90° and is connected with T component, and is used for interfering with the set signal according to the direction-finding azimuth, four azimuth plane direction-finding antenna array is composed of four pairs of antennas, and is used for interferometer direction-finding of the set signal; Positioning module is used for receiving positioning signals, and provides positioning information and time reference for the system; Gyroscope is used for self-positioning of the system attitude, and provides the angle deviation information of the device relative to the north for the system; Direction-finding receiver is composed of calibration source module, frequency source module and multiple phase coherent frequency conversion receiving modules, is used for interferometer direction-finding of the signals received by the direction-finding antenna array, and gives the direction of the set signal, calibration source module simultaneously inputs the signal source for T component, forms the interference signal on the required frequency, and frequency source module provides multiple frequency sources for direction-finding receiver, general monitoring receiver and calibration module, including fixed frequency and variable frequency source; General monitoring receiver monitors the signals output by the omnidirectional monitoring antenna, measures the signal frequency, bandwidth and pulse parameters after finding the set signal; Digital processing module is connected with instantaneous frequency measurement receiver, general monitoring receiver and direction-finding receiver respectively, and processes the signals of the receivers.

2. The ultra-wideband detection and tracking integrated antenna system of claim 1, wherein, The T component comprises SPST, push amplifier, power divider, phase shifter, attenuator, push amplifier, power amplifier and isolator, the input is input into the push amplifier after passing through the SPST, the push amplifier outputs to the power divider, the power divider divides the output signal into multiple output signals with equal amplitude and equal phase, and each output signal is sequentially output after passing through the phase shifter, the attenuator, the push amplifier, the power amplifier and the isolator.

3. The ultra-wideband covert reconnaissance antenna system of claim 1, wherein: The system further comprises an active front end, the active front end is close to the antenna and comprises an amplitude limiter, a filter, a first SPDT switch, a second SPDT switch, a low-noise amplifier and an attenuator, the input signal is sequentially output after passing through the amplitude limiter, the filter, the first SPDT switch, the low-noise amplifier, the second SPDT switch and the attenuator, and the first SPDT switch and the second SPDT switch are directly connected.

4. The ultra-wideband covert reconnaissance antenna system of claim 1, wherein, The system further comprises a signal switching module, the signal switching module is used for switching and selecting the signals of the four azimuth plane transmitting antenna array and direction-finding antenna array, and outputs to the T component, the direction-finding receiver or the general monitoring receiver, the signal switching module comprises four SP4T switches and is used for switching the azimuth of the four azimuth plane direction-finding antennas; Sixteen SP4T switches are used for selecting the four azimuth plane transmitting phased array antennas.

5. The ultra-wideband covert reconnaissance antenna system of claim 1, wherein, The phase tracking frequency conversion receiving module comprises a limiter, a SPDT, a first digital control attenuator, a first switch filter group, a low noise amplifier, a first mixer, a second switch filter group, a second digital control attenuator, a first amplifier, a second mixer, a second amplifier, a third digital control attenuator, a digital control phase shifter, a third amplifier and a third switch filter group. The calibration input is connected through the SPDT. The radio frequency input reaches the first mixer through the limiter, the SPDT, the first digital control attenuator, the first switch filter group and the low noise amplifier. The second local oscillator input reaches the first mixer. After being processed by the first mixer, the signal reaches the second mixer through the second switch filter group, the second digital control attenuator and the first amplifier in sequence. The first local oscillator input reaches the second mixer. After being processed by the second mixer, the signal reaches the third switch filter group through the second amplifier, the third digital control attenuator, the digital control phase shifter, the third amplifier and the third switch filter group in sequence. The signal is output after being processed by the third switch filter group.

6. The ultra-wideband covert reconnaissance antenna system of claim 1, wherein, The general monitoring receiver adopts the same structure as the phase tracking frequency conversion receiving module, comprising a limiter, a first digital control attenuator, a first switch filter group, a low noise amplifier, a first mixer, a second switch filter group, a second digital control attenuator, a first amplifier, a second mixer, a second amplifier, a third digital control attenuator, a digital control phase shifter, a third amplifier and a third switch filter group. The radio frequency input reaches the first mixer through the limiter, the first digital control attenuator, the first switch filter group and the low noise amplifier. The second local oscillator input reaches the first mixer. After being processed by the first mixer, the signal reaches the second mixer through the second switch filter group, the second digital control attenuator and the first amplifier in sequence. The first local oscillator input reaches the second mixer. After being processed by the second mixer, the signal reaches the third switch filter group through the second amplifier, the third digital control attenuator, the digital control phase shifter, the third amplifier and the third switch filter group in sequence. The signal is output after being processed by the third switch filter group.

7. The ultra-wideband covert reconnaissance antenna system of claim 1, wherein, The calibration module adopts the same structure as the phase tracking frequency conversion receiving module, comprising a first digital control attenuator, a first switch filter group, a low noise amplifier, a first mixer, a second switch filter group, a second digital control attenuator, a first amplifier, a second mixer, a second amplifier, a third digital control attenuator, a digital control phase shifter, a third amplifier and a third switch filter group. The intermediate frequency signal input reaches the second mixer through the third switch filter group, the third amplifier, the digital control phase shifter, the third digital control attenuator and the second amplifier in sequence. The first local oscillator input reaches the second mixer. After being processed by the second mixer, the signal reaches the first mixer through the first amplifier, the second digital control attenuator and the second switch filter group in sequence. The second local oscillator input reaches the first mixer. After being processed by the first mixer, the signal is output after being processed by the low noise amplifier, the first switch filter group and the first digital control attenuator in sequence.

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