Fiber-coupled terahertz transceiver system

Abstract

This document describes a transmission network, network elements, and usage methods, including a transmitter comprising a client-side input, a transmitter circuitry, and an antenna. The client-side input is configured to receive a baseband signal encoded with client data. The transmitter circuitry is configured to receive the baseband signal from the client-side input and generate an antenna feed signal based on the baseband signal. The antenna is configured to receive the antenna feed signal from the transmitter circuitry, generate a radiated signal based on the antenna feed signal, and couple the radiated signal into a hollow waveguide. Each radiated signal is a radiated electromagnetic wave configured for coherent detection and having a frequency in the range of 300 GHz to 10 THz.

Description

Cross-references to related applications

[0001] This application is filed pursuant to Section 119(e) of Title 35 of the United States Code, against provisional applications filed June 4, 2024, with U.S. Serial No. 63 / 655,823; against provisional applications filed June 10, 2024, with U.S. Serial No. 63 / 658,162; against provisional applications filed June 10, 2024, with U.S. Serial No. 63 / 658,176; and against provisional applications filed June 18, 2024. The entire contents of provisional application number 63 / 661,437, provisional application number 63 / 666,886 (filed July 2, 2024), provisional application number 63 / 575,162 (filed April 5, 2024), and provisional application number 63 / 593,874 (filed October 27, 2023) are incorporated herein by reference. Background Technology

[0002] Optical networking is a communication method that uses light-coded signals to transmit information across various types of telecommunications networks, including limited-range local area networks (LANs) and wide area networks (WANs). It is a form of optical communication that relies on optical amplifiers, lasers or LEDs, and wavelength division multiplexing (WDM) to typically transmit large amounts of data across fiber optic cables. Because it can achieve extremely high bandwidth, it is an enabling technology for the Internet and telecommunications networks, transmitting the vast majority of all human-to-machine and machine-to-machine information. However, further development and optimization of optical networking systems face certain limitations, namely power consumption, thermal requirements, and mechanical tolerances.

[0003] Optical components generate photons by exciting electrons in a gain medium, and these electrons emit photons when they return to a lower energy level. Despite efforts to improve efficiency, optical components generate a certain amount of heat during the electron excitation process, a phenomenon known as power dissipation. Excessive power dissipation can lead to thermal management problems and may affect the performance and lifespan of optical components.

[0004] Optical components are sensitive to temperature fluctuations and typically require lower operating temperatures than purely electronic components to maintain optimal performance. Increased temperatures can lead to increased signal noise, degraded signal quality, and a shortened lifespan for optical components. Therefore, optical components usually require cooling systems (e.g., heat sinks, fans, or thermoelectric devices) to dissipate excess heat and keep the optical components within safe temperature ranges.

[0005] Optical networking systems typically operate at micrometer wavelengths, demanding extremely high precision in component manufacturing, assembly, and alignment. Even slight deviations from required mechanical tolerances can lead to signal degradation, loss, or the introduction of optical crosstalk, negatively impacting network performance. Achieving and maintaining the necessary mechanical tolerances requires advanced manufacturing techniques and stringent quality control measures. Summary of the Invention

[0006] This paper discloses the transmission network, network components, and usage methods. Issues related to power consumption, thermal requirements, and mechanical tolerances are addressed through a terahertz (THz) radio frequency (RF) transmission system, in which the RF signal is coupled into a hollow waveguide for transmission.

[0007] In terms of power consumption, RF transceivers lack optical components, thus eliminating the power requirements associated with activating the optics and generating photons. Furthermore, the transmission of RF signals in the THz band involves longer wavelengths than the transmission of optical signals in higher frequency bands, meaning less energy is needed to create and modulate the signal. Finally, no photoelectric conversion is required because the RF transceiver operates entirely in the electronic domain. Therefore, power consumption is reduced in fiber-coupled THz RF transceiver systems. RF transceivers also require less stringent thermal requirements because they lack temperature-sensitive optical components. As a result, temperature control and DC bias control are unnecessary. Moreover, due to the less stringent thermal requirements, RF transceivers can be more easily integrated into existing processes or technologies. In terms of mechanical tolerances, the antenna does not require precise alignment of the optics (i.e., coupling an RF signal into a hollow waveguide requires lower precision than coupling an optical signal into a hollow waveguide). Furthermore, operating in the THz band means that the transmitted signal has a much longer wavelength, which also helps to relax mechanical tolerances. Finally, in terms of spectral efficiency, RF systems are generally more efficient than optical systems, thus allowing for increased throughput.

[0008] In one aspect, this disclosure includes a transmitter comprising: a client-side input configured to receive one or more baseband signals therein encoded with client data; a transmitter circuitry configured to receive the one or more baseband signals from the client-side input and generate one or more antenna feed signals based on the one or more baseband signals; and one or more antennas configured to receive the one or more antenna feed signals from the transmitter circuitry, generate one or more radiated signals based on the one or more antenna feed signals, and couple the one or more radiated signals into a hollow waveguide, each of the one or more radiated signals being a radiated electromagnetic wave configured for coherent detection and having a frequency in the range of 300 GHz and 10 THz.

[0009] In another aspect, this disclosure includes a receiver comprising: one or more antennas configured to detect one or more radiated signals received from a hollow waveguide and to generate one or more antenna output signals based on the one or more radiated signals, each of the one or more radiated signals being a radiated electromagnetic wave configured for coherent detection, having a frequency in the range of 300 GHz and 10 THz, and wherein client data is encoded therein; a receiver circuitry configured to receive the one or more antenna output signals from the one or more antennas and to generate one or more baseband signals based on the one or more antenna output signals; and a client-side output configured to receive the one or more baseband signals from the receiver circuitry and to transmit the one or more baseband signals.

[0010] In another aspect, this disclosure includes a transmission network comprising: one or more hollow waveguides; a transmitter including: a client-side input configured to receive one or more first baseband signals encoded therein; a transmitter circuitry configured to receive the one or more first baseband signals from the client-side input and generate one or more antenna feed signals based on the one or more first baseband signals; and one or more first antennas configured to receive the one or more antenna feed signals from the transmitter circuitry, generate one or more radiated signals based on the one or more antenna feed signals, and couple the one or more radiated signals to at least one of the one or more hollow waveguides, each of the one or more radiated signals being configured for coherent detection. And having radiated electromagnetic waves with frequencies in the range of 300 GHz to 10 THz; and a receiver comprising: one or more second antennas configured to detect the one or more radiated signals received from at least one of the one or more hollow waveguides, and to generate one or more antenna output signals based on the one or more radiated signals; a receiver circuitry configured to receive the one or more antenna output signals from the one or more second antennas, and to generate one or more second baseband signals based on the one or more antenna output signals, the one or more second baseband signals having the client data; and a client-side output configured to receive the one or more second baseband signals from the receiver circuitry and to transmit the one or more second baseband signals.

[0011] On the other hand, this disclosure includes a transceiver comprising: a transmitter including: a client-side input configured to receive one or more first baseband signals having first client data; a transmitter circuitry configured to receive the one or more first baseband signals from the client-side input and generate one or more antenna feed signals based on the one or more first baseband signals; and one or more first antennas configured to receive the one or more antenna feed signals from the transmitter circuitry, generate one or more first radiated signals based on the one or more antenna feed signals, and radiate the one or more first radiated signals. A first radiated signal is coupled into a first hollow waveguide, each of the one or more first radiated signals being configured for coherent detection and having a first frequency in the range of 300 GHz and 10 THz; and a receiver comprising: one or more second antennas configured to detect one or more second radiated signals received from one of the first and second hollow waveguides, and to generate one or more antenna output signals based on the one or more second radiated signals, each of the one or more second radiated signals being a radiated electromagnetic wave configured for coherent detection, having a second frequency in the range of 300 GHz and 10 THz, and having second client data; a receiver circuitry configured to receive the one or more antenna output signals from the one or more second antennas, and to generate one or more second baseband signals based on the one or more antenna output signals; and a client-side output configured to receive the one or more second baseband signals from the receiver circuitry and to transmit the one or more second baseband signals. Attached Figure Description

[0012] The accompanying drawings, which are incorporated in and constitute a part of this specification, illustrate one or more embodiments described herein and explain these embodiments together with the specification. The drawings are not intended to be drawn to scale, and for clarity and brevity, certain features and views may be shown enlarged or schematically. Not every component can be labeled in every drawing. The same reference numerals in the drawings may indicate and refer to the same or similar elements or functions. In the drawings:

[0013] Figure 1 This is a schematic diagram of the electromagnetic (EM) spectrum.

[0014] Figure 2 This is a block diagram of an exemplary implementation of a transmission network constructed in accordance with the present disclosure.

[0015] Figure 3A It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of an exemplary embodiment of the first hollow waveguide shown.

[0016] Figure 3B It is a cut along line 3-3' in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide has no optional dielectric layer.

[0017] Figure 3C It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide has no optional support layer.

[0018] Figure 3D It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide does not have an optional dielectric layer and an optional support layer.

[0019] Figure 3E It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a photonic bandgap fiber.

[0020] Figure 3F It is a cut along line 3-3' in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide has a hollow waveguide core having an elliptical cross-section.

[0021] Figure 3G It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the hollow waveguide core of the first hollow waveguide has a rectangular cross-section.

[0022] Figure 3H It is a cut along line 3-3' in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the hollow waveguide core of the first hollow waveguide has a square cross-section.

[0023] Figure 3I It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the hollow waveguide core of the first hollow waveguide has a cross-shaped cross-section.

[0024] Figure 3JIt is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a solid rod optical fiber.

[0025] Figure 3K It is a cut along line 3-3' in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a microstructured optical fiber.

[0026] Figure 3L It is a cut along line 3-3' in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a porous optical fiber.

[0027] Figure 3M It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a suspended porous core optical fiber.

[0028] Figure 3N It is a cut along line 3-3' in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a suspended open-slot core optical fiber.

[0029] Figure 3O It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a hollow core bandgap optical fiber.

[0030] Figure 3P It is a cut along line 3-3' in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a hollow core optical fiber.

[0031] Figure 3Q It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a hollow core optical fiber with negative curvature.

[0032] Figure 3R It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is based on a hollow core optical fiber with anti-resonance and suppression coupling.

[0033] Figure 3SIt is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a hollow core nested anti-resonant nodeless optical fiber.

[0034] Figure 3T It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a 3D-printed hollow core optical fiber based on anti-resonance and suppression coupling.

[0035] Figure 3U It is a cut along line 3-3′ in the direction of the arrow. Figure 2 A cross-sectional view of another exemplary embodiment of the first hollow waveguide shown, wherein the first hollow waveguide is a Bragg fiber.

[0036] Figure 4A yes Figure 2 A block diagram of an exemplary implementation of the first transmitter shown.

[0037] Figure 4B yes Figure 2 A block diagram of another exemplary embodiment of the first transmitter shown, wherein the first transmitter includes a serializer.

[0038] Figure 4C yes Figure 2 A block diagram of another exemplary embodiment of the first transmitter shown, wherein the first transmitter includes a deserializer.

[0039] Figure 4D yes Figure 4A A block diagram of an exemplary embodiment of the transmitter circuit system shown.

[0040] Figure 4E yes Figure 4A A block diagram of another exemplary embodiment of the transmitter circuit system shown, wherein the transmitter circuit system includes a combiner.

[0041] Figure 4F yes Figure 2 A block diagram of another exemplary embodiment of the first transmitter shown.

[0042] Figure 4G yes Figure 2 A block diagram of another exemplary embodiment of the first transmitter shown.

[0043] Figure 5A yes Figure 2 A block diagram of an exemplary embodiment of the first receiver shown.

[0044] Figure 5B yes Figure 2 A block diagram of another exemplary embodiment of the first receiver shown, wherein the first receiver includes a deserializer.

[0045] Figure 5C yes Figure 2 A block diagram of another exemplary embodiment of the first transmitter shown, wherein the first transmitter includes a serializer.

[0046] Figure 5D yes Figure 5A A block diagram of an exemplary embodiment of the receiver circuit system shown.

[0047] Figure 5E yes Figure 5A A block diagram of another exemplary embodiment of the receiver circuit system shown, wherein the receiver circuit system includes a splitter.

[0048] Figure 5F yes Figure 2 A block diagram of another exemplary embodiment of the first receiver shown.

[0049] Figure 5G yes Figure 2 A block diagram of another exemplary embodiment of the first receiver shown.

[0050] Figure 6A yes Figure 2 A block diagram illustrating an exemplary embodiment of the transceiver.

[0051] Figure 6B yes Figure 2 A block diagram of another exemplary embodiment of the transceiver shown.

[0052] Figure 7 This is a schematic diagram of a folded modulator constructed according to the present disclosure.

[0053] Figure 8 This is a schematic diagram of a rectifier detector constructed in accordance with the present disclosure.

[0054] Figure 9A This is a side view of an exemplary embodiment of an antenna for generating circularly polarized signals constructed in accordance with the present disclosure.

[0055] Figure 9B yes Figure 9A A side view of another exemplary embodiment of the antenna shown.

[0056] Figure 10 yes Figure 9A A perspective view of another exemplary embodiment of the antenna shown, wherein the antenna is a two-wire helical antenna.

[0057] Figure 11 yes Figure 10 The diagram shows a perspective view of another exemplary embodiment of the dual-wire spiral antenna, wherein the dual-wire spiral antenna is enclosed within a conductive cone.

[0058] Figure 12 It is a section taken along line 12-12′ and in the direction of the arrow. Figure 11 The diagram shows a partial cross-sectional view of the dual-wire spiral antenna.

[0059] Figure 13 It is enclosed in Figure 12 A schematic diagram of the electric field generated by the double-wire spiral antenna inside the conductive cone shown.

[0060] Figure 14 It is closed in Figure 12 A schematic diagram of the radiation pattern of a double-wire spiral antenna within a conductive cone.

[0061] Figure 15 This is a side view of an exemplary embodiment of a non-uniform bilinear spiral antenna constructed in accordance with the present disclosure.

[0062] Figure 16 This is a side view of another exemplary embodiment of a non-uniform double-helix antenna.

[0063] Figure 17 yes Figure 15 A graphical view of the polarization decoupling of a non-uniform double-wire spiral antenna.

[0064] Figure 18 yes Figure 16 A graphical view of the polarization decoupling of a non-uniform double-wire spiral antenna.

[0065] Figure 19 This is a side view of another exemplary embodiment of a non-uniform double-helix antenna.

[0066] Figure 20 This is a side view of another exemplary embodiment of a non-uniform double-helix antenna.

[0067] Figure 21 This is a schematic diagram of an exemplary embodiment of a differential waveguide probe antenna constructed in accordance with the present disclosure.

[0068] Figure 22A It is the section along line 22-22′ and in the direction of the arrow. Figure 21 The diagram shows a partial cross-sectional view of the differential waveguide probe antenna.

[0069] Figure 22B It is a section taken along line 23-23′ in the direction of the arrow. Figure 22A Another partial cross-sectional view of the differential waveguide probe antenna shown.

[0070] Figure 22C It is a section taken along line 24-24′ in the direction of the arrow. Figure 22B Another partial cross-sectional view of the differential waveguide probe antenna shown.

[0071] Figure 22D yes Figure 21 The diagram shows a graphical view of the polarization decoupling of the differential waveguide probe antenna.

[0072] Figure 23 This is a schematic diagram of an exemplary embodiment of a differential conical antenna constructed in accordance with the present disclosure.

[0073] Figure 24A It is the section along line 27-27′ and in the direction of the arrow. Figure 23 The diagram shows a partial cross-sectional view of the differential conical antenna.

[0074] Figure 24B It is cut from line 28-28′ in the direction of the arrow. Figure 24A Another partial cross-sectional view of the differential conical antenna shown.

[0075] Figure 24C yes Figure 23 A graphical view of the polarization decoupling of the differential conical antenna shown.

[0076] Figure 25 This is a schematic diagram of an exemplary embodiment of a differential microstrip patch antenna constructed in accordance with the present disclosure.

[0077] Figure 26 This is a schematic diagram of an exemplary embodiment of a single-ended waveguide probe antenna constructed in accordance with the present disclosure.

[0078] Figure 27A It is a section taken along line 55-55′ in the direction of the arrow. Figure 26 The diagram shows a cross-sectional view of a single-ended waveguide probe antenna.

[0079] Figure 27B It is a section taken along line 56-56′ in the direction of the arrow. Figure 26 Another cross-sectional view of the single-ended waveguide probe antenna shown.

[0080] Figure 27C It is a section taken along line 57-57′ in the direction of the arrow. Figure 27B The diagram shows a partial cross-sectional view of a single-ended waveguide probe antenna.

[0081] Figure 28 This is a schematic diagram of an exemplary embodiment of a slot antenna constructed in accordance with the present disclosure.

[0082] Figure 29A It is the section along line 59-59′ and in the direction of the arrow. Figure 28The cross-sectional view of the slot antenna is shown.

[0083] Figure 29B It is a cut along the line 60-60′ and in the direction of the arrow. Figure 29A The diagram shows a partial cross-sectional view of the slot antenna.

[0084] Figure 29C It is a section taken along line 61-61′ in the direction of the arrow. Figure 29A Another partial cross-sectional view of the slot antenna shown.

[0085] Figure 30A It is the section along line 59-59′ and in the direction of the arrow. Figure 28 A cross-sectional view of another embodiment of the slot antenna shown, wherein the slot antenna is a double-slot antenna.

[0086] Figure 30B It is a section taken along line 63-63′ in the direction of the arrow. Figure 30A The diagram shows a partial cross-sectional view of the slot antenna.

[0087] Figure 30C It is a section taken along line 64-64′ in the direction of the arrow. Figure 30A Another partial cross-sectional view of the slot antenna shown.

[0088] Figure 31 This is a schematic diagram of another exemplary embodiment of a transmission network constructed in accordance with the present disclosure.

[0089] Figure 32A yes Figure 31 A schematic diagram of an exemplary embodiment of the transmitter shown.

[0090] Figure 32B yes Figure 31 A schematic diagram of an exemplary embodiment of the receiver shown.

[0091] Figure 33 yes Figure 31 A schematic diagram of an exemplary embodiment of the antenna array shown.

[0092] Figure 34 This is a schematic diagram of another exemplary embodiment of a transmission network constructed in accordance with the present disclosure.

[0093] Figure 35A yes Figure 34 The diagram illustrates an exemplary embodiment of the antenna array, wherein the first antenna, the second antenna, the third antenna, and the fourth antenna are arranged in an n×m grid pattern.

[0094] Figure 35B yes Figure 34The diagram shows another exemplary embodiment of the antenna array, in which the first antenna, the second antenna, the third antenna, and the fourth antenna are arranged in a 1×m grid pattern.

[0095] Figure 36 Is using Figure 31 A schematic diagram of the transmission network method shown.

[0096] Figure 37A This is a schematic diagram of an exemplary embodiment of a dual-polarization (dual-pol) network element constructed in accordance with the present disclosure.

[0097] Figure 37B This is a schematic diagram of another exemplary embodiment of a dual-pol network element constructed in accordance with the present disclosure.

[0098] Figure 38 This is a graphical view of the dual POL signal according to the present disclosure.

[0099] Figure 39 This is a schematic diagram of an exemplary embodiment of a dual-pol transmission network constructed according to the present disclosure, wherein the dual-pol transmission network includes dual-pol RF antennas.

[0100] Figure 40 This is a schematic diagram of another exemplary embodiment of a dual-pol transmission network constructed according to the present disclosure, wherein the dual-pol transmission network includes a first pair of RF antennas and a second pair of RF antennas.

[0101] Figure 41 This is a schematic diagram of another exemplary embodiment of a dual-pol transmission network constructed according to the present disclosure, wherein the dual-pol transmission network includes a plurality of first RF antennas and a plurality of second RF antennas.

[0102] Figure 42 yes Figure 37A A schematic diagram of an exemplary embodiment of the first modulator shown.

[0103] Figure 43 yes Figure 37B A schematic diagram of an exemplary embodiment of the first demodulator shown.

[0104] Figure 44 This is a schematic diagram of another exemplary embodiment of a dual-pol network element constructed according to the present disclosure, wherein the dual-pol network element includes an equalizer.

[0105] Figure 45 This is a diagram illustrating how to use the content of this disclosure.

[0106] Figure 46AThis is a schematic diagram of another exemplary embodiment of a network element constructed according to the present disclosure, wherein the network element is configured to perform a direct conversion from a first modulation format in a first electrical signal to a second modulation format in a second electrical signal in a THz frequency band.

[0107] Figure 46B This is a schematic diagram of another exemplary embodiment of a network element constructed according to the present disclosure, wherein the network element is configured to perform a direct conversion from a first modulation format to a second modulation format in a THz frequency band and includes an RF antenna.

[0108] Figure 47A yes Figure 46A A schematic diagram of an exemplary embodiment of the demodulator shown.

[0109] Figure 47B This is a schematic diagram of another exemplary embodiment of a demodulator constructed according to the present disclosure, wherein the demodulator includes a clock and data recovery circuit (CDR).

[0110] Figure 48 yes Figure 47A A schematic diagram of an exemplary embodiment of the first phase demodulator shown.

[0111] Figure 49 yes Figure 47A A schematic diagram of an exemplary embodiment of the first amplitude demodulator shown.

[0112] Figure 50A yes Figure 46A and 46B A schematic view of an exemplary embodiment of the modulator shown.

[0113] Figure 50B yes Figure 46A and 46B The diagram shows another exemplary embodiment of the modulator, wherein the modulator includes a local oscillator (LO) generator.

[0114] Figure 51 This is a schematic diagram of an exemplary embodiment of a method for performing direct modulation from a first modulation format to a second modulation format in an electrical signal in the THz frequency band.

[0115] Figure 52 yes Figure 50A and 50B The diagram illustrates an exemplary embodiment of the first phase modulator, wherein the first phase modulator includes a cross switch.

[0116] Figure 53A yes Figure 50A and 50BA schematic diagram of an exemplary embodiment of the first amplitude modulator shown, wherein the first amplitude modulator includes a PI-type switching attenuator.

[0117] Figure 53B yes Figure 50A and 50B A schematic diagram of another exemplary embodiment of the first amplitude modulator shown, wherein the first amplitude modulator includes a T-switch attenuator.

[0118] Figure 53C yes Figure 50A and 50B A schematic diagram of another exemplary embodiment of the first amplitude modulator shown, wherein the first amplitude modulator includes a bridged T-switch attenuator.

[0119] Figure 54 This is a schematic diagram of another exemplary embodiment of a transceiver constructed in accordance with the present disclosure.

[0120] Figure 55 This is a schematic diagram of another exemplary embodiment of a transceiver constructed in accordance with the present disclosure.

[0121] Figure 56 This is a schematic diagram of another exemplary embodiment of a transceiver constructed in accordance with the present disclosure.

[0122] Figure 57 This is a schematic diagram of another exemplary embodiment of a transmitter constructed in accordance with the present disclosure.

[0123] Figure 58 This is a schematic view of another exemplary embodiment of a receiver constructed in accordance with the present disclosure.

[0124] Figure 59 This is a schematic view of another exemplary embodiment of a transmitter constructed in accordance with the present disclosure.

[0125] Figure 60 This is a schematic diagram of another exemplary embodiment of a transmitter constructed in accordance with the present disclosure.

[0126] Figure 61 This is a schematic diagram of an exemplary embodiment of a differential circuit constructed in accordance with the present disclosure.

[0127] Figure 62 yes Figure 61 A schematic diagram of another exemplary embodiment of the differential circuit shown.

[0128] Figure 63 yes Figure 61 A schematic diagram of another exemplary embodiment of the differential circuit shown.

[0129] Figure 64 This is a schematic diagram of another exemplary embodiment of an antenna array constructed in accordance with the present disclosure.

[0130] Figure 65 This is a perspective view of an exemplary embodiment of an electromagnetic absorber used and constructed according to this disclosure.

[0131] Figure 66 This is a cross-sectional view of another exemplary embodiment of an electromagnetic absorber constructed according to the present disclosure.

[0132] Figure 67 This is a cross-sectional view of another exemplary embodiment of an electromagnetic absorber constructed according to the present disclosure.

[0133] Figure 68 This is a cross-sectional view of another exemplary embodiment of an electromagnetic absorber constructed according to the present disclosure.

[0134] Figure 69 This is a schematic diagram of another exemplary embodiment of an electromagnetic absorber constructed in accordance with the present disclosure.

[0135] Figure 70 This is a flowchart illustrating an exemplary implementation of the process according to the present disclosure.

[0136] Figure 71 This is a flowchart of another exemplary embodiment of the process according to this disclosure; and

[0137] Figure 72 This is a process flow diagram of an exemplary embodiment of the construction process constructed in accordance with the present disclosure. Detailed Implementation

[0138] The following detailed description refers to the accompanying drawings. The same reference numerals in different drawings may identify the same or similar elements.

[0139] As used herein, the terms “comprises,” “comprising,” “includes,” “including,” “has,” “having,” or any other variation thereof are intended to cover non-exclusive inclusion. For example, a process, method, article, or apparatus that comprises a list of elements is not necessarily limited to those elements, but may include other elements not expressly listed or inherent to such process, method, article, or apparatus. Furthermore, unless expressly stated to the contrary, “or” means inclusive or, not exclusive, or. For example, any of the following satisfy conditions A or B: A is true (or exists) and B is false (or does not exist); A is false (or does not exist) and B is true (or exists); and both A and B are true (or exist).

[0140] Additionally, the terms "a" or "an" are used to describe elements and components of the implementations herein. This is done merely for convenience and to give a general meaning to the inventive concept. The description should be understood to include one or more, and the singular includes the plural, unless clearly otherwise indicated. The term "implementation" as used herein is synonymous with the term "implementation method".

[0141] Furthermore, the use of the term "multiple" implies "more than one" unless there is an explicit statement to the contrary.

[0142] As used herein, qualifiers such as “basically,” “about,” “approximately,” and their combinations and variations are intended to include not only the exact quantity or value they define, but also some slight deviations from it, which may be due to, for example, manufacturing tolerances, measurement errors, wear and tear, stresses applied to the individual parts, and their combinations.

[0143] The use of the terms “at least one” or “one or more” shall be understood to include one as well as any number of more than one. Furthermore, the use of the phrase “at least one of X, V, and Z” shall be understood to include only X, only V, and only Z, as well as any combination of X, V, and Z.

[0144] The use of ordinal terms (i.e., “first,” “second,” “third,” “fourth,” etc.) is for the purpose of distinguishing two or more items only, and unless otherwise expressly stated, does not imply any order or sequence or importance of one item relative to another or any additional order.

[0145] Finally, as used herein, any reference to "one embodiment" or "implementation" means that a particular element, feature, structure, or characteristic described in connection with that embodiment is included in at least one embodiment. The phrase "in one embodiment" appearing in various places throughout the specification does not necessarily refer to the same embodiment.

[0146] As used herein, unless the context explicitly states otherwise, all numerical values ​​or ranges include values ​​within those ranges and fractions of integers within those ranges. Thus, for the sake of illustration, references to numerical ranges such as 1-10 include 1, 2, 3, 4, 5, 6, 7, 8, 9, 10 and 1.1, 1.2, 1.3, 1.4, 1.5, etc. Similarly, references to ranges from 1-50 include 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13, 14, 15, 16, 17, 18, 19, 20, etc., up to and including 50, and 1.1, 1.2, 1.3, 1.4, 1.5, etc., 2.1, 2.2, 2.3, 2.4, 2.5, etc. References to a series of ranges include ranges of values ​​that combine the boundaries of different ranges within that series. Therefore, for the purposes of this explanation, references to a range of ranges, such as 1 to 10, 10-20, 20 to 30, 30-40, 40 to 50, 50 to 60, 60 to 75, 75-100, 100-150, 150-200, 200-250, 250-300, 300-400, 400-500, 500-750, 750-1,000, are included, for example, the ranges of 1 to 20, 10-50, 50-100, 100-500, and 500-1,000.

[0147] As used herein, "circuit system" can refer to analog and / or digital components, or one or more appropriately programmed processors (e.g., microprocessors) and associated hardware and software, or hardwired logic. Furthermore, a "component" can perform one or more functions. The term "component" can include hardware such as processors (e.g., microprocessors), combinations of hardware and software, etc. Software can include one or more processor-executable instructions that, when executed by one or more processors, cause one or more processors to perform a specified function. It should be understood that the algorithms described herein can be stored on one or more non-transitory memories. Exemplary non-transitory memories can include random access memory, read-only memory, flash memory, etc. Such non-transitory memories can be electrical, optical, etc.

[0148] As used in this article, a “mode” refers to a unique distribution of electric and magnetic fields that repeats along the length of a hollow waveguide, through which electromagnetic energy can be transmitted. “Single-mode” refers to a hollow waveguide designed to carry only one mode of electromagnetic wave. This is achieved by having a narrow core diameter, which allows only one mode of light to propagate at a time. On the other hand, “multimode” refers to a hollow waveguide designed to carry multiple modes of electromagnetic waves simultaneously. This is possible due to its larger core diameter, enabling the propagation of multiple modes.

[0149] As used in this article, “amplitude modulation” (AM) refers to a form of signal modulation in which data is encoded in the amplitude of a carrier signal.

[0150] As used in this article, “Amplitude Shift Keying” (ASK) refers to a form of AM in which digital data is encoded in the amplitude of a carrier signal, and each symbol (i.e., representing one or more data bits) is transmitted by sending a fixed-amplitude carrier at a fixed frequency over a specific time period.

[0151] As used in this article, “Phase Shift Keying” (PSK) is a form of signal modulation in which signal data is encoded in the phase of a carrier signal with a constant frequency. “Orthogonal PSK” (PSK) is a form of PSK in which two data bits (i.e., 00, 01, 10, or 11) are modulated at once, selecting one of four possible carrier phase shifts (i.e., 0°, 90°, 180°, or 270°).

[0152] As used herein, “Pulse Amplitude Modulation” (PAM) refers to a form of AM in which the data signal is encoded in the amplitude of a series of carrier signal pulses. “PAM4” refers to a form of PAM in which the data signal is encoded in the amplitude of a series of carrier signal pulses, wherein the amplitude of the carrier signal pulses can be one of four discrete values ​​(i.e., 0, 1, 2, or 3), and each carrier signal pulse represents two data bits (i.e., 00, 01, 10, or 11).

[0153] As used herein, “non-return-to-zero” (NRZ) refers to a form of signal modulation in which binary data signals are encoded in a carrier signal such that 1 is represented by a first valid condition (e.g., positive voltage) and 0 is represented by a second valid condition (e.g., negative voltage). “Inverse non-return-to-zero” (NRZI) refers to a form of signal modulation in which data bits are represented by the presence or absence of transitions at clock boundaries.

[0154] As used herein, “Quadrature Amplitude Modulation” (QAM) refers to a form of AM in which two analog message signals or two digital bit streams are encoded using ASK or AM with amplitudes of two carriers, and the two carrier signals are 90° out of phase with each other. “QAM16” refers to a form of QAM in which the carrier signals can exist in one of sixteen discrete states (i.e., symbols), having one of sixteen different amplitude and phase levels representing four data bits (i.e., from 0000 to 1111).

[0155] As used in this article, "Trench-coded modulation" (TCM) refers to a form of signal modulation in which binary data signals are encoded into the phase of a constant-amplitude carrier signal. The transmitted signal is created by convolutionally encoding the binary data signal and mapping the result to a signal constellation.

[0156] As used in this article, the "Rayleigh range" refers to the distance along the direction of beam propagation from the waist to the point where the cross-sectional area doubles.

[0157] As used herein, a “hollow waveguide” refers to a structure that guides waves by restricting the transmission of energy in a particular direction. In the context of this disclosure, a “hollow waveguide” can refer to an optical fiber having a waveguide core operable to propagate RF signals in the THz band or a routing waveguide operable to propagate RF signals in the THz band.

[0158] As used herein, "diameter" refers to a straight line passing through the center of the subject or graphic from one side to the other. In some embodiments, the subject or graphic has a circular or elliptical shape.

[0159] As used herein, “data” refers to the quantity, characters, or symbols on which a computer performs operations. Data can be recorded on non-transitory computer-readable media, such as random access memory and / or read-only memory. Random access memory and / or read-only memory can be implemented on semiconductor, magnetic, optical, or mechanical recording media. An example of data is client data, such as data provided by a client in conjunction with telecommunications services and / or storage services.

[0160] Now refer to the attached diagram, especially Figure 1 The illustration shows a schematic diagram of an electromagnetic (EM) spectrum 100 according to this disclosure. This disclosure generally relates to network elements that communicate using radiated signals comprising radiated electromagnetic waves coupled to a hollow waveguide. The radiated signals described herein typically have a transmission frequency in what is referred to as the terahertz (THz) band 104 (i.e., frequencies between 0.1 THz and 10 THz corresponding to wavelengths between 3 millimeters (mm) and 30 micrometers (μm). However, in some embodiments described herein, the transmission frequency of the radiated signal is in the range between 300 gigahertz (GHz) and 10 THz. The radiated signals described herein are typically configured for coherent detection and typically have a bandwidth in the range between 10% and 40% of the transmission frequency.

[0161] Now for reference Figure 2The diagram illustrates a block diagram of an exemplary embodiment of a transmission network 200 (hereinafter referred to as "transmission network 200") constructed according to the present disclosure. The transmission network 200 is depicted as including a plurality of network elements 204a-n (hereinafter referred to as "network elements 204") (e.g., Figure 2 The first network element 204a, the second network element 204b, the third network element 204c, and the fourth network element 204d are shown. Although for illustrative purposes... Figure 2 Only four network elements 204 are shown in the diagram, but it should be understood that the transport network 200 may include multiple network elements 204, which may be more or less than four.

[0162] The transmission network 200 may also include one or more hollow waveguides 208a-n (hereinafter referred to as "hollow waveguide 208") (e.g., Figure 2 The first hollow waveguide 208a, the second hollow waveguide 208b, the third hollow waveguide 208c, and the fourth hollow waveguide 208d are shown. Although for illustrative purposes... Figure 2 Only four hollow waveguides 208 are shown in the diagram, but it should be understood that the transmission network 200 may include multiple hollow waveguides 208, which may be more or less than four.

[0163] Within the transmission network 200, radiated signals transmitted from the first network element 204a to the fourth network element 204d or vice versa can travel along (1) a first path formed by the first hollow waveguide 208a, the second network element 204b, and the second hollow waveguide 208b, or (2) a second path formed by the third hollow waveguide 208c, the third network element 204c, and the fourth hollow waveguide 208d.

[0164] In some embodiments, each hollow waveguide 208 is configured to support the propagation of a radiated signal in only a single direction. However, in other embodiments, one or more hollow waveguides 208 may be configured to support the propagation of a radiated signal in multiple directions (i.e., two opposite directions). In embodiments where one or more hollow waveguides 208 are configured to support the propagation of a radiated signal in multiple directions, a first radiated signal propagating through the hollow waveguide 208 in a first direction can be distinguished from a second radiated signal propagating through the hollow waveguide 208 in a second direction opposite to the first direction by being provided with different polarizations, frequencies, etc. In some such embodiments, one or more circulators may be included to achieve this distinction.

[0165] Each network element 204 may include one or more of the following: transmitter 212 (e.g., Figure 2The first transmitter 212a and the second transmitter 212b shown are operable to transmit a radiated signal including radiated electromagnetic waves encoded therein via a hollow waveguide 208; the receiver 216 (e.g., Figure 2 The first receiver 216a and the second receiver 216b shown are operable to receive radiated signals including radiated electromagnetic waves encoded therein via hollow waveguide 208; and / or transceiver 220 (e.g., Figure 2 The first transceiver 220a shown in the figure and Figure 6B The second transceiver 220b shown is operable to transmit a first radiated signal, including a first radiated electromagnetic wave encoded with first client data, via a specific hollow waveguide in the hollow waveguide 208, and / or receive a second radiated signal, including a second radiated electromagnetic wave encoded with second client data, via other hollow waveguides in the hollow waveguide 208.

[0166] Each network element 204 may also include a control module 224 (e.g., Figure 2 The first control module 224a, the second control module 224b, the third control module 224c, and the fourth control module 224d shown (collectively referred to as "control module 224") are operable to adjust one or more operating parameters of the network element 204 to which the control module 224 is coupled.

[0167] In some embodiments, one or more network elements 204 may communicate with each other via a communication network 228. The communication network 228 may allow bidirectional communication of information and / or data between one or more network elements 204 of the transmission network 200. The communication network 228 may interface with one or more network elements 204 in various ways. For example, in some embodiments, the communication network 228 may interface via optical and / or electronic interfaces, and / or may use multiple network topologies and / or protocols, including but not limited to Ethernet, TCP / IP, circuit-switched paths, combinations thereof, etc. The communication network 228 may utilize various network protocols to allow bidirectional interface and / or communication of data and / or information between one or more network elements 204.

[0168] Communication network 228 can be virtually any type of network. For example, in some embodiments, communication network 228 can be a version of the Internet (e.g., existing in a TCP / IP-based network). In one embodiment, communication network 228 is the Internet. However, it should be noted that communication network 228 can be virtually any type of network and can be implemented as the World Wide Web (i.e., the Internet), a Local Area Network (LAN), a Wide Area Network (WAN), a Metropolitan Area Network, a wireless network, a cellular network, a Bluetooth network, a Global System for Mobile Communications (GSM) network, a Code Division Multiple Access (CDMA) network, a 3G network, a 4G network, an LTE network, a 5G network, a satellite network, a radio network, an optical network, a wired network, a public switched telephone network, an Ethernet network, a combination thereof, etc.

[0169] If the communication network 228 is the Internet, the main user interface of the transmission network 200 can be delivered through a series of web pages or private internal web pages of a company or enterprise. These web pages or private internal web pages can be written in Hypertext Markup Language, JavaScript, etc., and can be accessed by users. It should be noted that the main user interface of the transmission network 200 can be another type of interface, including but not limited to Windows-based applications, form-based applications, mobile web interfaces, VR-based applications, applications running on mobile devices, etc. In one embodiment, the communication network 228 can be connected to one or more network elements 204.

[0170] Figure 2 The number of devices and / or networks shown is provided for illustrative purposes. In reality, with... Figure 2 Compared to what is shown, there may be additional equipment and / or networks, fewer equipment and / or networks, different equipment and / or networks, or equipment and / or networks with different arrangements. Furthermore, Figure 2 The two or more devices shown can be implemented within a single device, or Figure 2 The single device shown can be implemented as multiple distributed devices. Additionally or alternatively, one or more devices of the transport network 200 can perform one or more functions described as being performed by another one or more devices of the transport network 200.

[0171] Network element 204 can take many different forms. For example, network element 204 can be an integrated circuit (IC). In this example, network element 204 (e.g., IC) can communicate via a hollow waveguide 208 via a signal comprising radiated electromagnetic waves having client data encoded therein, without requiring an electrical data bus. In other embodiments, network element 204 can be incorporated into components in a data center, such as servers, routers, switches, firewalls, storage systems, application delivery controllers, etc., to establish communication between such components in the data center via a signal comprising radiated electromagnetic waves having client data encoded therein propagated through the hollow waveguide 208. Thus, the hollow waveguide 208 can extend from one integrated circuit to another, or from one component to another, and this can be implemented in various ways, such as IC-to-IC communication, printed circuit board (PCB)-to-PCB communication, component-to-component communication, and / or combinations thereof. In the PCB-to-PCB communication example, network element 204 may each comprise a PCB.

[0172] Now for reference Figures 3A-3H And 4A-4L, which shows the section along line 3-3′ and intercepted in the direction of the arrow. Figure 2 Cross-sectional views of various exemplary embodiments of the first hollow waveguide 208a shown. However, it should be understood that reference... Figures 3A-3H The descriptions of 4A-4L are applicable to any hollow waveguide 208 described herein. Figures 3A-3H In the embodiments shown in 4A-4L, the first hollow waveguide 208a is a hollow optical fiber. However, it should be understood that in other specific embodiments, the first hollow waveguide 208a may be another form of hollow waveguide, such as, for example, a substrate-integrated waveguide.

[0173] The first hollow waveguide 208a (and therefore each hollow waveguide 208) typically includes a hollow waveguide core 304 and a tubular sidewall 306 having, in some embodiments, defining the hollow waveguide core 304, or in other embodiments simply surrounding the inner surface 312 of the hollow waveguide core 304.

[0174] Typically, the hollow waveguide core 304 can be made of any material capable of radiating electromagnetic waves within the THz frequency band 104 or, in some embodiments, within the range of 300 GHz and 10 THz. More specifically, the hollow waveguide core 304 can be made of any material having low absorption loss (i.e., absorption loss in the range of 1 dB / km and 10,000 dB / km) within the THz frequency band 104 or, in some embodiments, within the range of 300 GHz and 10 THz.

[0175] In some embodiments, the hollow waveguide core 304 may be made of a polymer (e.g., cyclic olefin polymer (COP), cyclic olefin copolymer (COC), polytetrafluoroethylene (PTFE), high-density polyethylene (HDPE), polymethylpentene (PMP), polypropylene (PP), polystyrene, polycarbonate, poly(methyl methacrylate) (PMMA), Picarlin or ultraviolet (UV) resin) or glass (e.g., quartz glass, crown glass or borosilicate glass).

[0176] In other embodiments, the hollow waveguide core 304 may be composed of gas, vacuum, or a porous material (i.e., a material with a porosity in the range of 25% to 99%). In such embodiments, the hollow waveguide core 304 may have a refractive index, for example, in the range of 1.0 to 1.4. As discussed in more detail below, the hollow waveguide core 304 may have a refractive index n1.

[0177] In some embodiments, the hollow waveguide core 304 may have a cross section configured to support the propagation of a radiated signal having only a single polarization at a given time. However, in other embodiments, the hollow waveguide core 304 may have a cross section configured to support the propagation of a radiated signal having multiple polarizations at a given time. In either case, the hollow waveguide core 304 may have a cross section configured to support the propagation of a radiated signal having one or more linear polarizations or one or more circular polarizations.

[0178] In some embodiments, the hollow waveguide core 304 may have a cross section configured to support the propagation of a radiated signal having only a single mode at a given time. However, in other embodiments, the hollow waveguide core 304 may have a cross section configured to support the propagation of a radiated signal having multiple modes at a given time.

[0179] The tubular sidewall 306 of the first hollow waveguide 208a (and therefore each hollow waveguide 208) may include a conductive layer 316 surrounding the hollow waveguide core 304. Figure 3A-3I (as shown in the diagram), a dielectric layer 308 optionally disposed between the hollow waveguide core 304 and the conductive layer 316 (in... Figure 3A , 3C (as shown in 3F-3I), and optionally a support layer 320 surrounding the conductive layer 316 (in Figure 3A , 3B (As shown in 3E-3I).

[0180] In some embodiments, the tubular sidewall 306 of the first hollow waveguide 208a (and therefore each hollow waveguide 208) may include a plurality of conductive layers 316 interleaved with the plurality of dielectric layers 308.

[0181] In some embodiments, the tubular sidewall 306 of the first hollow waveguide 208a (and therefore each hollow waveguide 208) may also include one or more strength members (not shown) (hereinafter referred to as "strength members") surrounding the conductive layer 316, which are configured to enhance the elasticity of the first hollow waveguide 208a. In such embodiments, a support layer 320 may surround the strength members.

[0182] Typically, the conductive layer 316 can be made of any material with a refractive index n3 greater than the refractive index (i.e., n1) of the hollow waveguide core 304. More specifically, the conductive layer 316 can be made of a non-oxide metal material (e.g., silver, gold, or indium tin oxide (ITO)). Providing a conductive layer 316 with a refractive index greater than that of the hollow waveguide core 304 can improve the effective refractive index of the first hollow waveguide 208a. The increase in n results in more radiated signals being confined and propagated within the hollow waveguide core 304.

[0183] Typically, in embodiments where the dielectric layer 308 is disposed between the conductive layer 316 and the hollow waveguide core 304, the dielectric layer 308 can be made of any material with a refractive index n2 greater than the refractive index (i.e., n1) of the hollow waveguide core 304. More specifically, the dielectric layer 308 can be made of polymers (e.g., cyclic olefin polymers (COP), cyclic olefin copolymers (COC), polytetrafluoroethylene (PTFE), high-density polyethylene (HDPE), polymethylpentene (PMP), polypropylene (PP), polystyrene, polycarbonate, poly(methyl methacrylate) (PMMA), Picarlin, or ultraviolet (UV) resin) or glass (e.g., silica glass, crown glass, or borosilicate glass), but in this embodiment, a material with a refractive index n2 greater than the refractive index (i.e., n1) of the hollow waveguide core 304 is particularly preferred. Providing a dielectric layer 308 with a refractive index greater than that of the hollow waveguide core 304 can improve the effective refractive index of the first hollow waveguide 208a. The increase in n results in more radiated signals being confined and propagated within the hollow waveguide core 304.

[0184] The support layer 320 can be configured to shield the inner layer of the first hollow waveguide 208a (and thus any hollow waveguide 208) from external environmental factors, provide flexibility to the first hollow waveguide 208a, and / or enhance the tensile strength of the first hollow waveguide 208a. In some embodiments, the support layer 320 may be made of a polymer material, such as an acrylate polymer or polyimide.

[0185] In some embodiments, the cross-section of the hollow waveguide core 304 may have a circular shape (i.e., having a diameter d1 equal along the x-axis and y-axis) (in Figures 3A-3D(As shown in the figure). In some such embodiments, the diameter d1 of the hollow waveguide core 304 can be between 30 μm and 6 mm. In some such embodiments, the diameter d1 of the hollow waveguide core 304 can be between 30 μm and 3 mm. In at least one such embodiment, the diameter d1 of the hollow waveguide core 304 can be 1 mm.

[0186] In some implementations, such as Figure 3E As shown, the first hollow waveguide 208a may be a photonic bandgap fiber, which includes a plurality of air channels 324 (hereinafter referred to as "air channels 324") periodically spaced apart throughout the conductive layer 316.

[0187] In other embodiments, the cross-section of the hollow waveguide core 304 may have, for example, an elliptical shape (i.e., having a first diameter x1 along the x-axis and a second diameter y1 along the y-axis, wherein the first diameter is not equal to the second diameter) (e.g. Figure 3F As shown), rectangular shape (such as...) Figure 3G As shown) (i.e., having a first length x1 along the x-axis and a second length y1 along the y-axis, where the first length is not equal to the second length), a square shape (i.e., having a length l1 equal to both the x-axis and the y-axis) (as shown) Figure 3H (as shown) or a cross-shaped shape (i.e., having a length l1 equal to both the x-axis and y-axis) (as shown) Figure 3I (As shown).

[0188] In other embodiments, the first hollow waveguide 208a (and therefore any hollow waveguide 208) can be implemented as, for example, a solid rod optical fiber. Figure 3J As shown), microstructured optical fiber ( Figure 3K As shown), porous optical fiber ( Figure 3L As shown), suspended porous core optical fiber ( Figure 3M As shown), suspended open-slot core optical fiber ( Figure 3N As shown), hollow bandgap fiber ( Figure 3O As shown), hollow tube optical fiber ( Figure 3P (as shown), hollow-core optical fiber with negative curvature ( Figure 3Q As shown), hollow-core optical fiber based on anti-resonance and suppression coupling ( Figure 3R As shown), hollow-core nested anti-resonant nodeless fiber ( Figure 3S As shown), hollow optical fiber based on anti-resonance and suppression coupling 3D printing ( Figure 3T (as shown) or Bragg fiber ( Figure 3U (As shown).

[0189] Now for reference Figure 4A , which shows Figure 2A block diagram of an exemplary embodiment of the first transmitter 212a is shown. However, it should be understood that the description of any particular transmitter 212 is applicable to any of the transmitters 212 described herein. The first transmitter 212a (and therefore each of the transmitters 212) typically includes: a client-side input 400 configured to receive one or more baseband signals 404 (hereinafter referred to as "baseband signals 404") encoded therein from one or more external components (e.g., control module 224); a transmitter circuitry 408 configured to receive the baseband signals 404 from the client-side input 400 and generate one or more antenna feed signals 412 (hereinafter referred to as "antenna feed signals 412") based on the baseband signals 404; and one or more first antennas 416 configured to receive the antenna feed signals 412 from the transmitter circuitry 408, generate one or more radiated signals 420 (hereinafter referred to as "radiated signals 420") based on the antenna feed signals 412, and couple the radiated signals 420 into a first hollow waveguide 208a.

[0190] In some implementations, client-side input 400 is a pair of inputs configured to receive differential signals. In some such implementations, client-side input 400 may be a Low Voltage Differential Signaling (LVDS) link configured to receive LVDS signals, and baseband signal 404 may be an LVDS signal indicating client data.

[0191] In some embodiments, the antenna feed signal 412 is provided to the first antenna 416 on one or more transmission lines (not shown) (hereinafter referred to as "transmission lines"), wherein each transmission line has two or more conductors (not shown) (hereinafter referred to as "conductors"). In some embodiments, the transmission line has a first transmission loss, and the first hollow waveguide 208a has a second transmission loss less than the first transmission loss. In some embodiments, the second transmission loss is in the range of 0.001 to 20.00 dB / m / Tb / s.

[0192] In some specific implementations, such as Figure 4AAs shown, each of the client-side input 400, transmitter circuitry 408, and first antenna 416 may be disposed on substrate 424. However, in other embodiments, one or more of the client-side input 400, transmitter circuitry 408, and first antenna 416 may be disposed on the first substrate (not shown), and one or more of the client-side input 400, transmitter circuitry 408, and first antenna 416 may not be disposed on the first substrate. For example, one or more of the client-side input 400, transmitter circuitry 408, and first antenna 416 may be disposed on a second substrate (not shown). In such embodiments, the first and second substrates may be arranged in a stacked configuration.

[0193] In some embodiments, substrate 424 may have multiple layers (not shown). In such an embodiment, one or more of client-side input 400, transmitter circuitry 408, and first antenna 416 may be disposed on a first layer (not shown), and one or more of client-side input 400, transmitter circuitry 408, and first antenna 416 may be disposed on a second layer (not shown).

[0194] In some embodiments, one or more of the client-side input 400, transmitter circuitry 408, and first antenna 416 may be integrated into a single semiconductor die (not shown). In some specific embodiments, one or more of the client-side input 400, transmitter circuitry 408, and first antenna 416 may be implemented using one or more of complementary metal-oxide-semiconductor (CMOS) technology, silicon-germanium (SiGe) semiconductor technology, and III-V compound semiconductor technology.

[0195] In some implementations, baseband signal 404 is a digital bitstream. In some implementations, client data can be encoded in baseband signal 404 using an encoding protocol that conforms to one or more of Return-to-Zero (RZ) code, Non-Return-to-Zero (NRZ) code, Pulse Amplitude Modulation (PAM), and Quadrature Amplitude Modulation (QAM). In some implementations, client data can be encoded in radiated signal 420 using an encoding protocol that conforms to one or more of RZ, NRZ, Quadrature Phase Shift Keying (QPSK), QAM, Ternary Coded Modulation (TCM), and Bose-Chaudhuri-Hocquenghem (BCH) code.

[0196] In some embodiments, the radiated signal 420 includes a first complementary radiated signal (not shown) having a first polarization and a second complementary radiated signal (not shown) having a second polarization different from the first polarization. In such an embodiment, the first antenna 416 may be configured to generate the radiated signal 420 including the first and second complementary radiated signals based on an antenna feed signal 412. The first and second polarizations may be orthogonal to each other.

[0197] In some embodiments, each of the first polarization and the second polarization may be linear polarization. In such specific embodiments, the first antenna 416 may include one or more of a differential waveguide probe antenna, a differential tapered antenna, and a differential patch antenna. In other embodiments, each of the first polarization and the second polarization may be circular polarization. In such embodiments, the first antenna 416 may include one or more of a helical antenna and a spiral antenna. It should be understood that any signal described herein may be a single-ended signal or a differential signal.

[0198] In some embodiments, the radiated signal 420 includes a first complementary radiated signal (not shown) having a first polarization and a second complementary radiated signal (not shown) having a second polarization different from the first polarization, and the first antenna 416 is further configured to couple the first and second complementary radiated signals into a first hollow waveguide 208a such that the first and second complementary radiated signals interact in the first hollow waveguide 208a to form a combined radiated signal (not shown) having a third polarization different from the first and second polarizations. In such embodiments, the first antenna 416 may include an antenna array.

[0199] Now for reference Figure 4B In some embodiments, the first transmitter 212a (and therefore any of the transmitters 212) further includes a first serializer 426 configured to receive a plurality of parallel baseband signals 428a-n (hereinafter referred to as "parallel baseband signals 428") and combine the parallel baseband signals 428 into a serial baseband signal (i.e., baseband signal 404). In such embodiments, the client-side input 400 may be configured to receive the baseband signal 404 from the first serializer 426. In some such embodiments, the combination of the parallel baseband signals 428 into the baseband signal 404 utilizes at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM).

[0200] Now for reference Figure 4CIn some embodiments, the first transmitter 212a (and therefore any of the transmitters 212) further includes a first deserializer 432 configured to receive a serial baseband signal (i.e., baseband signal 404) and split the baseband signal 404 into parallel baseband signals 428. In such embodiments, the client-side input 400 may be configured to receive the parallel baseband signal 428 from the first deserializer 432. In some such embodiments, the baseband signal 404 is split into parallel baseband signals 428 using at least one of PDM, TDM, and WDM.

[0201] Now for reference Figure 4D , which shows Figures 4A-4C An exemplary embodiment of the transmitter circuit system 408 shown is illustrated. In some embodiments, the transmitter circuit 408 includes: one or more local oscillators 436a-n (hereinafter referred to as "LO436") configured to generate one or more carrier signals 440 (hereinafter referred to as "carrier signals 440") having a baseband frequency less than the transmission frequency; one or more modulation circuits 444 (hereinafter referred to as "modulator 444") configured to receive a baseband signal 404 from a client-side input 400 and a carrier signal 440 from LO 436, and modulate the baseband signal 404 onto the carrier signal 440 to generate one or more modulation signals 448 (hereinafter referred to as "modulator signals 448"); and one or more upconversion circuits 452 (hereinafter referred to as "upconverter 452") configured to receive the modulation signal 448 from the modulator 444 and upconvert the modulation signal 448 (i.e., increase the frequency of the modulation signal 448 from the baseband frequency to the transmission frequency) to generate an antenna feed signal 412.

[0202] Now for reference Figure 4E In an embodiment where the client-side input 400 is configured to receive the parallel baseband signal 428, the transmitter circuitry 408 can be configured to receive the parallel baseband signal 428 from the client-side input 400. In such an embodiment, the modulator 444 can be configured to receive the parallel baseband signal 428 from the client-side input 400 and the carrier signal 440 from the first LO 436, and modulate the parallel baseband signal 428 onto the carrier signal 440 to generate a modulated signal 448. In such an embodiment, the upconverter 452 can be configured to receive the modulated signal 448 from the modulator 444 and upconvert the modulated signal 448 to generate one or more upconverted signals 460 (hereinafter referred to as "upconverted signals 460").

[0203] In some embodiments, the transmitter circuitry 408 may further include a combiner 456 configured to receive the up-converted signal 460 from the upconverter 452 and combine the up-converted signal 460 into an antenna feed signal 412. However, in other embodiments, the first antenna 416 may be configured to receive the antenna feed signal 412 from the upconverter 452, generate a radiated signal 420 based on the antenna feed signal 412, and couple the radiated signal 420 into a first hollow waveguide 208a such that the radiated signals 420 interact within the first hollow waveguide 208a to form a combined radiated signal (not shown).

[0204] In some embodiments, the radiated signal 420 is coupled into a first hollow waveguide 208a such that the radiated signal 420 interacts in the first hollow waveguide 208a to form a combined radiated signal using at least one of PDM, TDM and WDM.

[0205] Now for reference Figure 4F , which shows Figure 2 A block diagram of another exemplary embodiment of the first transmitter 212a shown. However, it should be understood that the description of any particular transmitter 212 can be applied to any transmitter 212 described herein.

[0206] exist Figure 4F In the illustrated embodiment, the first transmitter 212a includes: a client-side input 400 configured to receive a baseband signal 404 from one or more external components (e.g., control module 224) and transmit the baseband signal 404 to a transmitter circuit 408; a transmitter circuit 408 configured to receive the baseband signal 404 from the client-side input 400, generate an antenna feed signal 412 based on the baseband signal 404, and transmit the antenna feed signal 412 to an RF interface 464, the RF interface 464 being configured to receive the antenna feed signal 412 from the transmitter circuit 408 and transmit the antenna feed signal 412; and a digital enhancement and control unit 468 configured to provide digital control and / or processing capabilities for one or more components of the first transmitter 212a.

[0207] exist Figure 4F In the embodiment shown, the transmitter circuit system 408 includes one or more modulation blocks 444a (hereinafter referred to as "modulation block 444a"), a frequency synthesizer 472 including a phase-locked loop (PLL) 476 and a first LO 436a, a second LO 436b, a first mixer 480a, a second mixer 480b, a first amplifier 484a and a second amplifier 484b.

[0208] Modulation block 444a can be configured to receive baseband signal 404 from client-side input 400 and encode baseband signal 404 in a format suitable for modulation onto carrier signal. In some embodiments, modulation block 444a may include one or more digital-to-analog converters (DACs), one or more serializers / deserializers (SerDes), and one or more folded modulators 700 (such as...). Figure 7 (As shown) and / or circuitry operable for encoding the baseband signal 404 in a modulation format (e.g., AM, ASK, PSK, QAM, QAM16, or variations thereof). In some embodiments, modulation block 444a may include circuitry operable to perform forward error correction (FEC). Modulation block 444a may also be configured to send an encoded input signal, in which data is encoded, to a second mixer 480b.

[0209] In some implementations, modulation block 444a is configured to simply receive baseband signal 404 (i.e., baseband signal 404 previously encoded in a modulation format) from client-side input 400 and send baseband signal 404 to second mixer 480b.

[0210] The second LO 436b can be configured to generate a second carrier signal with a continuous waveform (e.g., a sine wave) having a predetermined frequency (i.e., the baseband (BB) frequency). In some embodiments, the predetermined frequency (i.e., the BB frequency) of the second carrier signal is in the RF band (i.e., in the range between 30 Hz and 300 GHz). In some embodiments, the predetermined frequency (i.e., the BB frequency) of the second carrier signal is in the range between 1 MHz and 300 GHz. In some embodiments, the predetermined frequency (i.e., the BB frequency) of the second carrier signal is in the range between 5 GHz and 30 GHz. The second LO 436b can also be configured to transmit the second carrier signal to the second mixer 480b.

[0211] The second mixer 480b can be configured to receive an encoded baseband signal from the modulation block 444a, receive a second carrier signal from the second LO436b, upconvert the encoded baseband signal using the second carrier signal to generate a first modulated signal, wherein the first modulated signal is encoded with client data and has a predetermined frequency (i.e., BB frequency) of the second carrier signal, and send the first modulated signal to the third amplifier 484c.

[0212] The third amplifier 484c can be configured to receive a first modulation signal from the second mixer 480b, adjust the amplitude of the first modulation signal so that the amplified first modulation signal can drive the first mixer 480a, and send the amplified first modulation signal to the first mixer 480a.

[0213] Frequency synthesizer 472 (i.e., first LO 436a and PLL 476) can be configured to generate a first carrier signal having a continuous waveform (e.g., a sine wave) with a predetermined frequency (e.g., within THz band 104, or in some embodiments, in the range between 300 GHz and 10 THz). In some embodiments, the predetermined frequency of the first carrier signal is in the range between 30 GHz and 300 GHz. In some such embodiments, the predetermined frequency of the first carrier signal is 240 GHz. In other embodiments, the predetermined frequency of the first carrier signal is in the range between 300 GHz and 3 THz. Frequency synthesizer 472 can also be configured to send the first carrier signal to second amplifier 484b.

[0214] The second amplifier 484b can be configured to receive a first carrier signal from the first LO 436a, adjust the amplitude of the first carrier signal to generate an amplified carrier signal that can drive the first mixer 480a, and send the amplified carrier signal to the first mixer 480a.

[0215] The first mixer 480a may be configured to receive an amplified carrier signal from the second amplifier 484b, an amplified first modulation signal from the third amplifier 484c, upconvert the amplified first modulation signal using the amplified carrier signal to generate a second modulation signal, wherein the second modulation signal is encoded with client data and has a predetermined frequency of the amplified carrier signal (i.e., within the THz band 104, or in some specific embodiments, within the range of 300 GHz and 10 THz), and transmit the second modulation signal to the first amplifier 484a.

[0216] The first amplifier 484a can be configured to receive a second modulation signal from the first mixer 480a, adjust the amplitude of the second modulation signal such that the amplified second modulation signal can be transmitted via the RF interface 464, and send the amplified second modulation signal to the RF interface 464. For example, the first amplifier 484a can be configured to generate the amplified second modulation signal with a power in the range of 0.05 watts (W) to 0.4 W.

[0217] RF interface 464 can be configured to receive an amplified second modulated signal encoded with client data from a first amplifier 484a, and transmit the amplified second modulated signal as an antenna feed signal 412 (i.e., encoded with client data) within a predetermined frequency range (e.g., THz band 104, or in some embodiments, between 300 GHz and 10 THz). In some embodiments, RF interface 464 can be electrically connected to one of the first antennas 416 and configured to transmit the antenna feed signal 412 to the first antenna 416. However, in other embodiments, the first antenna 416 may be included instead of RF interface 464.

[0218] Now for reference Figure 4G , which shows Figure 2 A block diagram of another exemplary embodiment of the first transmitter 212a shown. Figure 5B In the illustrated embodiment, the first transmitter 212a includes multiple inputs, including an in-phase (I)-BB client-side input 400a and a quadrature (Q)-BB client-side input 400b configured to receive I-BB baseband signals 404a and 404b from one or more external components (e.g., control module 224), respectively, and an LO input 400c configured to receive one or more carrier signals 488 (hereinafter referred to as "carrier signals 488") from an external LO. The transmitter circuitry 408 is configured to generate an antenna feed signal 412 based on the I-BB baseband signals 404a, 404b, and 488, and the RF interface 464 is configured to transmit the antenna feed signal 412.

[0219] exist Figure 4G In the illustrated embodiment, the transmitter circuit system 408 includes a balun 492, a third mixer 480c, a fourth mixer 480d, a fifth mixer 480e, and a sixth mixer 480f, a fourth amplifier 484d, a fifth amplifier 484e, a sixth amplifier 484f, a seventh amplifier 484g, and an eighth amplifier 484h, an orthogonal coupler (e.g., a branch-line coupler) 494, and a power combiner (e.g., a Wilkinson power combiner) 498.

[0220] The I-BB baseband signal 404a and Q-BB baseband signal 404b can be the I and Q components of the baseband signal 404, which encodes client data. The I-BB client-side input 400a can be configured to send the I-BB baseband signal 404a to the sixth amplifier 484f. The Q-BB client-side input 400b can be configured to send the Q-BB baseband signal 404b to the seventh amplifier 484g.

[0221] The LO input 400c can be configured to receive a carrier signal 488 from an external LO, the carrier signal 488 having a continuous waveform (e.g., a sine wave) at a predetermined frequency. The LO input 400c can also be configured to transmit the carrier signal 488 to the Balun 492.

[0222] Balun 492 can be configured to isolate and / or maintain the impedance difference between balanced and unbalanced transmission lines. Balun 492 can also be configured to send a carrier signal 488 to a third mixer 480c.

[0223] The third mixer 480c can be configured to receive a carrier signal 488 from the Balun 492, multiply the carrier signal 488 (e.g., by a multiple of four), and send the multiplied carrier signal to the fourth amplifier 484d.

[0224] The fourth amplifier 484d can be configured to receive the multiplied carrier signal from the third mixer 480c, adjust the amplitude of the multiplied carrier signal so that the amplified carrier signal can drive the fourth mixer 480d, and send the amplified carrier signal to the fourth mixer 480d.

[0225] The fourth mixer 480d can be configured to receive an amplified carrier signal from the fourth amplifier 484d, multiply the amplified carrier signal (e.g., by a multiple of 2), and send the re-multiplied carrier signal to the fifth amplifier 484e.

[0226] The fifth amplifier 484e can be configured to receive the remultiplied carrier signal from the fourth mixer 480d, adjust the amplitude of the remultiplied carrier signal so that the reamplified carrier signal can drive the quadrature coupler 494, and send the reamplified carrier signal to the quadrature coupler 494.

[0227] The sixth amplifier 484f can be configured to receive the I-BB baseband signal 404a from the I-BB client side input 400a, adjust the amplitude of the I-BB baseband signal 404a so that the amplified I-BB input signal can drive the fifth mixer 480e, and send the amplified I-BB signal to the fifth mixer 480e.

[0228] The seventh amplifier 484g can be configured to receive the Q-BB baseband signal 404b from the Q-BB client side input 400b, adjust the amplitude of the Q-BB baseband signal 404b so that the amplified Q-BB baseband signal 404b can drive the sixth mixer 480f, and drive the amplified Q-BB signal to the sixth mixer 480f.

[0229] The quadrature coupler 494 can be configured to receive a reamplified carrier signal from the fifth amplifier 484e, split the reamplified carrier signal into a first carrier signal and a second carrier signal, send the first carrier signal to the fifth mixer 480e, and send the second carrier signal to the sixth mixer 480f, wherein the first carrier signal and the second carrier signal are out of phase by 90°.

[0230] The fifth mixer 480e can be configured to receive an amplified I-BB signal from the sixth amplifier 484f, receive a first carrier signal from the quadrature coupler 494, upconvert the amplified I-BB signal using the first carrier signal to generate an I-antenna feed signal having a predetermined frequency of the carrier signal 488, in which the I component of the client data is encoded, and the I-antenna feed signal is sent to the power combiner 498.

[0231] The sixth mixer 480f can be configured to receive an amplified Q-BB signal from the seventh amplifier 484g, receive a second carrier signal from the quadrature coupler 494, upconvert the amplified Q-BB signal using the second carrier signal to generate a Q antenna feed signal, wherein the Q component of the client data is encoded and has a predetermined frequency of the carrier signal 488, and send the Q antenna feed signal to the power combiner 498.

[0232] The power combiner 498 can be configured to receive an I-antenna feed signal from a fifth mixer 480e, a Q-antenna feed signal from a sixth mixer 480f, combine the I-antenna feed signal and the Q-antenna feed signal to generate an antenna feed signal 412, and send the antenna feed signal 412 to an RF interface 464. In some embodiments, the RF interface 464 can be electrically connected to one of the first antennas 416 and configured to send the antenna feed signal 412 to the first antenna 416. However, in other embodiments, one of the first antennas 416 may be included instead of the RF interface 464.

[0233] Now for reference Figure 5A , which shows Figure 2A block diagram of an exemplary embodiment of the first receiver 216a (hereinafter referred to as "first receiver 216a") is shown. However, it should be understood that the description of any particular receiver 216 is applicable to any of the receivers 216 described herein. The first receiver 216a (and therefore each of the receivers 216) generally includes: one or more second antennas 516 configured to detect a radiated signal 420 received from a first hollow waveguide 208a and generate one or more antenna output signals 512 (hereinafter referred to as "antenna output signals 512") based on the radiated signal 420; a receiver circuitry 508 configured to receive the antenna output signals 512 from the second antenna 516 and generate a baseband signal 404 based on the antenna output signals 512; and a client-side output 500 configured to receive the baseband signal 404 from the receiver circuitry 508 and transmit the baseband signal 404 to one or more external components (e.g., control module 224).

[0234] In some embodiments, the antenna output signal 512 is received from the second antenna 516 on one or more transmission lines (not shown) (hereinafter referred to as "transmission lines"), wherein each transmission line has two or more conductors (not shown) (hereinafter referred to as "conductors"). In some embodiments, the transmission line has a first transmission loss, and the first hollow waveguide 208a has a second transmission loss less than the first transmission loss. In some embodiments, the second transmission loss is in the range of 0.001 and 20.00 dB / m / Tb / s.

[0235] In some implementations, such as Figure 5A As shown, each of the second antenna 516, receiver circuitry 508, and client-side output 500 can be disposed on substrate 524. However, in other embodiments, one or more of the second antenna 516, receiver circuitry 508, and client-side output 500 can be disposed on the first substrate (not shown), and one or more of the second antenna 516, receiver circuitry 508, and client-side output 500 may not be disposed on the first substrate. For example, one or more of the second antenna 516, receiver circuitry 508, and client-side output 500 can be disposed on a second substrate (not shown). In such specific embodiments, the first substrate and the second substrate may be arranged in a stacked configuration.

[0236] In some embodiments, substrate 524 may have multiple layers (not shown). In such an embodiment, one or more of the second antenna 516, receiver circuitry 508, and client-side output 500 may be disposed on a first layer (not shown), and one or more of the second antenna 516, receiver circuitry 508, and client-side output 500 may be disposed on a second layer (not shown).

[0237] In some embodiments, one or more of the second antenna 516, receiver circuitry 508, and client-side output 500 may be integrated into a single semiconductor die (not shown). In some embodiments, one or more of the second antenna 516, receiver circuitry 508, and client-side output 500 may be implemented using one or more of CMOS technology, SiGe semiconductor technology, and III-V compound semiconductor technology.

[0238] In some embodiments, the radiated signal 420 includes a first complementary radiated signal (not shown) having a first polarization and a second complementary radiated signal (not shown) having a second polarization different from the first polarization. In such an embodiment, the second antenna 516 can be configured to generate an antenna output signal 512 based on the radiated signal 420 including the first and second complementary radiated signals. The first and second polarizations can be orthogonal to each other.

[0239] In some embodiments, the radiated signal 420 may be formed from a first complementary radiated signal (not shown) having a first polarization interacting in the first hollow waveguide 208a and a second complementary radiated signal (not shown) having a second polarization different from the first polarization. In such embodiments, the radiated signal 420 may have a third polarization different from the first and second polarizations. In such embodiments, the second antenna 516 may be configured to generate an antenna output signal 512 based on the radiated signal 420 formed by the first and second complementary radiated signals.

[0240] Now for reference Figure 5B In some embodiments, the client-side output 500 is configured to receive a serial baseband signal (i.e., baseband signal 404) from the receiver circuitry 508. In such embodiments, the first receiver 216a (and therefore any receiver 216) may also include a second deserializer 526 configured to receive the baseband signal 404 from the client-side output 500, split the serial baseband signal into a parallel baseband signal 428, and transmit the parallel baseband signal 428 to one or more external components (e.g., control module 224). In some such embodiments, the serial baseband signal is split into the parallel baseband signal 428 using at least one of PDM, TDM, and WDM.

[0241] Now for reference Figure 5CIn some embodiments, the client-side output 500 is configured to receive the parallel baseband signal 428 from the receiver circuitry 508. In such embodiments, the first receiver 216a (and therefore any receiver 216) may also include a second serializer 532 configured to receive the parallel baseband signal 428 from the client-side output 500 and combine the parallel baseband signal 428 into a serial baseband signal (i.e., baseband signal 404). In some such embodiments, the parallel baseband signal 428 is combined into the baseband signal 404 using at least one of PDM, TDM, and WDM.

[0242] Now for reference Figure 5D , which shows Figures 5A-5C An exemplary embodiment of the receiver circuit system 508 shown is illustrated. In some embodiments, the receiver circuit system 508 includes: one or more LOs 536 (hereinafter referred to as "LO536") configured to generate one or more reference signals 540 (hereinafter referred to as "reference signals 540") having a baseband frequency less than the transmission frequency; one or more downconversion circuits 552 (hereinafter referred to as "downconverters 552") configured to receive an antenna output signal 512 from a second antenna 516 and receive the reference signals 540 from LO 536, and use the reference signals 540 to downconvert the antenna output signal 512 (i.e., reduce the frequency of the antenna output signal 512 from the transmission frequency to the baseband frequency) to generate one or more modulation signals 548 (hereinafter referred to as "modulation signals 548"); and one or more demodulation circuits 544 (hereinafter referred to as "demodulators 544") configured to receive the modulation signals 548 from the downconverters 552 and demodulate the modulation signals 548 to generate a baseband signal 404.

[0243] Now for reference Figure 5E In an embodiment where the second antenna 516 is configured to receive a radiation signal 420 formed by a first complementary radiation signal (not shown) having a first polarization interacting in the first hollow waveguide 208a and a second complementary radiation signal (not shown) having a second polarization different from the first polarization, the receiver circuitry 508 may be configured to receive an antenna output signal 512 from the second antenna 516. In such a specific embodiment, the demodulator 544 may be configured to receive a modulated signal 548 from the downconverter 552 and demodulate the modulated signal 548 to generate a parallel baseband signal 428.

[0244] In some embodiments, the receiver circuitry 508 may further include a splitter 556 configured to receive the antenna output signal 512 from the second antenna 516 and split the antenna output signal 512 into a plurality of parallel antenna output signals 560 (hereinafter referred to as "parallel antenna output signals 560"). However, in other embodiments, the second antenna 516 may be configured to detect a first complementary radiation signal and a second complementary radiation signal based on the radiation signal 420 received from the first hollow waveguide 208a, and to generate the antenna output signal 512 based on the first complementary radiation signal and the second complementary radiation signal.

[0245] In some implementations, the first complementary radiation signal and the second complementary radiation signal are detected using at least one of PDM, TDM and WDM based on the radiation signal 520 received from the first hollow waveguide 208a.

[0246] Now for reference Figure 5F , which shows Figure 2 A block diagram of another exemplary embodiment of the first receiver 216a shown. Figure 5F In the illustrated embodiment, the first receiver 216a includes an RF interface 564 configured to receive an antenna output signal 512, a receiver circuitry 508 configured to generate a baseband signal 404 based on the antenna output signal 512, a client-side output 500 configured to transmit the baseband signal 404 to one or more external components (e.g., control module 224), and a digital enhancement and control unit 568 configured to provide digital control and / or processing capabilities to one or more components of the first receiver 216a.

[0247] In the illustrated embodiment, the receiver circuit system 508 includes one or more demodulation blocks 544a (hereinafter referred to as "demodulation block 544a"), a frequency synthesizer 572 including a PLL 576 and a first LO 536a, a second LO 536b, a first mixer 580a, a second mixer 580b, a first amplifier 584a, a second amplifier 584b, and a third amplifier 584c.

[0248] RF interface 564 can be configured to transmit antenna output signal 512 to first amplifier 584a. In some embodiments, RF interface 564 can be configured to receive antenna output signal 512 from one of second antennas 516. In other embodiments, one of second antennas 516 may be included instead of RF interface 564.

[0249] The first amplifier 584a can be configured to receive the antenna output signal 512 from the RF interface 564, adjust the amplitude of the antenna output signal 512 so that the amplified transmission signal can drive the first mixer 580a, and send the amplified transmission signal to the first mixer 580a.

[0250] Frequency synthesizer 572 (i.e., first LO 536a and PLL 576) can be configured to generate a first carrier signal having a continuous waveform (e.g., a sine wave) with a predetermined frequency (e.g., within THz band 104, or in some embodiments, in the range between 300 GHz and 10 THz). In some embodiments, the predetermined frequency of the first carrier signal is in the range between 30 GHz and 300 GHz. In some such embodiments, the predetermined frequency of the first carrier signal is 240 GHz. In other embodiments, the predetermined frequency of the first carrier signal is in the range between 300 GHz and 3 THz. First LO 536a can also be configured to transmit the first carrier signal to second amplifier 584b.

[0251] The second amplifier 584b can be configured to receive a first carrier signal from the first LO 536a, adjust the amplitude of the first carrier signal to generate an amplified carrier signal that can drive the first mixer 580a, and send the amplified carrier signal to the first mixer 580a.

[0252] The first mixer 580a can be configured to receive the antenna output signal 512 from the first amplifier 584a, receive the amplified carrier signal from the second amplifier 584b, downconvert the antenna output signal 512 using the amplified carrier signal to generate a modulated signal in which client data is encoded and has a BB frequency, and send the modulated signal to the third amplifier 584c.

[0253] The third amplifier 584c can be configured to receive a modulation signal from the first mixer 580a, adjust the amplitude of the modulation signal so that the amplified modulation signal can drive the second mixer 580b, and send the amplified modulation signal to the second mixer 580b.

[0254] The second LO 536b can be configured to generate a second carrier signal having a continuous waveform (e.g., a sine wave) with a predetermined frequency (i.e., the BB frequency). In some embodiments, the predetermined frequency (i.e., the BB frequency) of the second carrier signal is in the range of 8 GHz and 10 GHz. The second LO 536b can also be configured to transmit the second carrier signal to the second mixer 580b.

[0255] The second mixer 580b can be configured to receive an amplified modulation signal from the third amplifier 584c, receive a second carrier signal from the second LO 536b, downconvert the amplified modulation signal using the second carrier signal to generate an encoded signal in which client data is encoded and has a predetermined frequency (i.e., BB frequency) of the second carrier signal, and send the encoded signal to the demodulation block 544a.

[0256] The demodulation block 544a can be configured to receive the encoded signal from the second mixer 580b and decode the encoded signal in a format suitable for transmission to one or more external components (e.g., control module 224) to generate the baseband signal 404.

[0257] In some implementations, demodulation block 544a may include one or more analog-to-digital converters (ADCs), one or more serializers / deserializers (SerDes), and one or more rectifier detectors 800 (e.g., Figure 8 The demodulation block 544a (shown) and / or circuitry operable to decode encoded output signals from modulation formats such as AM, ASK, PSK, QAM, or QAM16 or variations thereof, for example, to generate a baseband signal 404 in which client data is encoded. In some embodiments, the demodulation block 544a may include circuitry operable to perform forward error correction (FEC). The demodulation block 544a may also be configured to send the baseband signal 404 to the client-side output 500. In some embodiments, the demodulation block 544a is configured to simply receive the encoded signal from the second mixer 580b and send the encoded signal as the baseband signal 404 to the client-side output 500.

[0258] In some implementations, client-side output 500 is a pair of output interfaces. In some such implementations, client-side output 500 is an LVDS link configured to transmit LVDS signals, and baseband signal 404 is an LVDS signal in which client data is encoded.

[0259] Now for reference Figure 5G , which shows Figure 2 A block diagram of another exemplary embodiment of the first receiver 216a shown. Figure 5GIn the illustrated embodiment, the first receiver 216a includes an RF interface 564 configured to receive an antenna output signal 512, an LO input 500c configured to receive a carrier signal 588 from an external LO, a receiver circuit system 508 configured to generate a Q-BB baseband signal 404b and an I-BB baseband signal 404a based on the antenna output signal 512 and the carrier signal 588, and a Q-BB client-side output 500a and an I-BB client-side output 500b configured to transmit the Q-BB baseband signal 404b and the I-BB baseband signal 404a, respectively.

[0260] In the illustrated embodiment, receiver circuitry 508a includes a third mixer 580c, a fourth mixer 580d, a fifth mixer 580e, a sixth mixer 580f, a fourth amplifier 584d, a fifth amplifier 584e, a sixth amplifier 584f, a seventh amplifier 584g, an eighth amplifier 584h, a ninth amplifier 584i, a tenth amplifier 584j, an eleventh amplifier 584k, a twelfth amplifier 584l, a balun 592, an orthogonal coupler (e.g., a branch line coupler) 594, and a power divider (e.g., a Wilkinson power divider) 598.

[0261] The fourth amplifier 584d can be configured to receive the antenna output signal 512 from the RF interface 564, adjust the amplitude of the antenna output signal 512 so that the amplified transmitted signal can drive the power divider 598, and send the amplified transmitted signal to the power divider 598. In some embodiments, the fourth amplifier 584d is a low-noise amplifier (LNA).

[0262] The power divider 598 can be configured to receive the amplified transmission signal from the fourth amplifier 584d, split the amplified transmission signal into an I-antenna output signal in which the I component of the client data is encoded and a Q-antenna output signal in which the Q component of the client data is encoded, send the Q-antenna output signal to the third mixer 580c, and send the I-antenna output signal to the fourth mixer 580d.

[0263] The LO input 500c can be configured to receive a carrier signal 588 from an external LO, the carrier signal 588 having a continuous waveform (e.g., a sine wave) at a predetermined frequency. The LO input 500c can also be configured to transmit the carrier signal 588 to a Balun 592.

[0264] Balun 592 can be configured to isolate and / or maintain the impedance difference between balanced and unbalanced transmission lines. Balun 492 can also be configured to send a carrier signal 588 to a sixth mixer 580f.

[0265] The sixth mixer 580f can be configured to receive a carrier signal 588 from the Balun 592, multiply the carrier signal 588 (e.g., by a multiple of four), and send the multiplied carrier signal to the twelfth amplifier 584l.

[0266] The twelfth amplifier 584l can be configured to receive a multiplied carrier signal from the sixth mixer 580f, adjust the amplitude of the multiplied carrier signal to generate an amplified carrier signal that can drive the fifth mixer 580e, and send the amplified carrier signal to the fifth mixer 580e.

[0267] The fifth mixer 580e can be configured to receive an amplified carrier signal from the twelfth amplifier 584l, multiply the amplified carrier signal (e.g., by a multiple of two), and send the re-multiplied carrier signal to the eleventh amplifier 584k.

[0268] The eleventh amplifier 584k can be configured to receive a re-multiplied carrier signal from the fifth mixer 580e, adjust the amplitude of the re-multiplied carrier signal to generate a re-amplified carrier signal that can drive the quadrature coupler 594, and send the re-amplified carrier signal to the quadrature coupler 594.

[0269] The quadrature coupler 594 can be configured to receive a reamplified carrier signal from the eleventh amplifier 584k, split the reamplified carrier signal into a first carrier signal and a second carrier signal, send the first carrier signal to the third mixer 580c, and send the second carrier signal to the fourth mixer 580d, wherein the first carrier signal and the second carrier signal are out of phase by 90°.

[0270] The third mixer 580c can be configured to receive Q antenna output signals from the power divider 598, receive a first carrier signal from the quadrature coupler (e.g., a branch line coupler) 566, downconvert the Q antenna output signals with the first carrier signal to generate a Q-BB intermediate signal, wherein the Q component of the client data is encoded and has a BB frequency, and send the Q-BB intermediate signal to the fifth amplifier 584e.

[0271] The fifth amplifier 584e, the sixth amplifier 584f, and the seventh amplifier 584g can be configured to receive a Q-BB intermediate signal from the third mixer 580c, down-convert the Q-BB intermediate signal to generate a Q-BB baseband signal 404b, and send the Q-BB baseband signal 404b to the Q-BB client-side output 500a. In some embodiments, the fifth amplifier 584e is a transimpedance amplifier (TIA), and the sixth amplifier 584f is a variable gain amplifier (VGA).

[0272] The fourth mixer 580d can be configured to receive the I antenna output signal from the power divider 598, receive the second carrier signal from the quadrature coupler 594, use the second carrier signal to downconvert the I antenna output signal to generate an I-BB intermediate signal in which the I component of the client data is encoded and has the BB frequency, and send the I-BB intermediate signal to the eighth amplifier 584h.

[0273] The eighth amplifier 584h, the ninth amplifier 584i, and the tenth amplifier 584j can be configured to receive the I-BB intermediate signal from the fourth mixer 580d, down-convert the I-BB intermediate signal to generate the I-BB baseband signal 404a, and send the I-BB baseband signal 404a to the I-BB client-side output 500b. In some embodiments, the eighth amplifier 584h is a TIA, and the ninth amplifier 584i is a VGA.

[0274] Now for reference Figure 6A , which shows Figure 2 A block diagram illustrating an exemplary embodiment of the first transceiver 220a (hereinafter referred to as "first transceiver 220a"). However, it should be understood that the description of any particular transceiver 220 can be applied to any transceiver 220 described herein. The first transceiver 220a (and therefore each transceiver 220) typically includes a third transmitter 212c and a third receiver 216c.

[0275] The third transmitter 212c typically includes: a client-side input 600a configured to receive one or more first baseband signals 604a (hereinafter referred to as "first baseband signals 604a") encoded therein from one or more external components (e.g., control module 224); a transmitter circuitry 608a configured to receive the first baseband signals 604a from the client-side input 600a and generate one or more antenna feed signals 612a (hereinafter referred to as "antenna feed signals 612") based on the first baseband signals 604a; and one or more first antennas 616a (hereinafter referred to as "first antennas 616") configured to receive the antenna feed signals 612a from the transmitter circuitry 608a, generate one or more first radiated signals 420a (hereinafter referred to as "first radiated signals 420a") based on the antenna feed signals 612a, and couple the first radiated signals 420a into a fourth hollow waveguide 208d.

[0276] The third receiver 216c typically includes: one or more second antennas 616b (hereinafter referred to as "antenna 616b") configured to detect one or more second radiated signals 620b (hereinafter referred to as "second radiated signals 620b") received from the third hollow waveguide 208c, and generate one or more antenna output signals 612b (hereinafter referred to as "antenna output signals 612b") based on the second radiated signals 620b; a receiver circuitry 608b configured to receive the antenna output signals 612b from the second antenna 616b and generate a second baseband signal 604b based on the antenna output signals 612b; and a client-side output 600b configured to receive the second baseband signal 604b from the receiver circuitry 608b and transmit the second baseband signal 604b to one or more external components (e.g., control module 224).

[0277] Each component of the first transceiver 220a (and therefore each transceiver in the transceiver 220) may be identical or similar to one or more components of the first transmitter 212a and the first receiver 216a as described herein.

[0278] Now for reference Figure 6B , which shows Figure 2 A block diagram of another exemplary embodiment of the first transceiver 220a shown. Figure 6B In the illustrated embodiment, the first transceiver 220a includes a client-side input 600a configured to receive a first baseband signal 604a from one or more external components (e.g., control module 224), a transmitter circuitry 608a configured to generate an antenna feed signal 612a based on the input signal 640a, a first RF interface 664a configured to transmit the antenna feed signal 612a, a second RF interface 664b configured to receive an antenna output signal 612b, a receiver circuitry 608b configured to generate a second baseband signal 604b based on the antenna output signal 612b, a client-side output 600b configured to transmit the second baseband signal 604b to one or more external components, and a digital enhancement and control unit 668 configured to provide digital control and / or processing capabilities for one or more components of the first transceiver 220a.

[0279] In some embodiments, the first transceiver 220a includes a first RF interface 664a but lacks a second RF interface 664b. In such embodiments, the first RF interface 664a can be configured to transmit an antenna feed signal 612a and receive an antenna output signal 612b. In some embodiments, the first transceiver 220a may have more than two RF interfaces.

[0280] In the illustrated embodiment, the transmitter circuit system 608a includes a frequency synthesizer 672, which includes a PLL 676, a first LO 636a, a signal distribution block (e.g., a splitter) 698, one or more modulation blocks 644a (hereinafter referred to as "modulation block 644a"), a second LO 636b, a first mixer 680a, a third mixer 680c, a first amplifier 684a, a third amplifier 684c, and a fifth amplifier 684e.

[0281] In the illustrated embodiment, the receiver circuit system 608b includes a frequency synthesizer 672, a modulation block 644a, a third LO 636c, a second mixer 680b, a fourth mixer 680d, a second amplifier 684b, a fourth amplifier 684d, and a sixth amplifier 684f. The frequency synthesizer 672 includes a PLL 676, a first LO 636a, and a signal distribution block 698.

[0282] exist Figure 6B In some of the embodiments shown, each component of the first transceiver 220a is disposed on a single substrate 624, which may be part of a semiconductor wafer.

[0283] Modulation block 644a can be configured to: (1) receive a first baseband signal 604a from client-side input 600a, encode the first baseband signal 604a in a format suitable for modulation onto a carrier signal, and send the encoded input signal to a third mixer 680c; and (2) receive an encoded output signal from a fourth mixer 680d, decode the encoded output signal in a format suitable for transmission to one or more external components (e.g., control module 224), and send a second baseband signal 604b to client-side output 600b.

[0284] In some implementations, modulation block 644a may include one or more DACs, one or more ADCs, one or more serializers / deserializers (SerDes), and one or more folded modulators 700 (e.g., Figure 7 As shown), one or more rectifier detectors 800 (e.g.) Figure 8 (As shown) and / or a circuit system operable to encode the first baseband signal 604a in, for example, a modulation format (such as AM, ASK, PSK, QAM, or QAM16 or variations thereof), and to decode the encoded output signal from the modulation format to produce a second baseband signal 604b in which client data is encoded. In some embodiments, the modulation block 644a may include a circuit system operable to perform forward error correction (FEC).

[0285] Frequency synthesizer 672 can be configured to generate a first carrier signal having a continuous waveform (e.g., a sine wave) with a predetermined frequency (e.g., within THz band 104, or in some embodiments, between 300 GHz and 10 THz). In some embodiments, the predetermined frequency of the first carrier signal is between 30 GHz and 300 GHz. In some such embodiments, the predetermined frequency of the first carrier signal is 240 GHz. In other embodiments, the predetermined frequency of the first carrier signal is between 300 GHz and 3 THz. Frequency synthesizer 672 can also be configured to transmit the first carrier signal to signal distribution block 698.

[0286] The signal distribution block 698 can be configured to receive a first carrier signal from the first LO 636a and distribute the first carrier signal to the third amplifier 684c and the fourth amplifier 684d.

[0287] Referring now to transmitter circuitry 608a, in some embodiments, client-side input 600a is a pair of input interfaces. In some such embodiments, client-side input 600a is an LVDS link configured to receive LVDS signals, and a first baseband signal 604a is an LVDS signal in which client data is encoded. Client-side input 600a can also be configured to transmit the first baseband signal 604a to modulation block 644a.

[0288] The second LO 636b can be configured to generate a second carrier signal with a continuous waveform (e.g., a sine wave) having a predetermined frequency (i.e., the BB frequency). In some embodiments, the predetermined frequency (i.e., the BB frequency) of the second carrier signal is in the range of 8 GHz and 10 GHz. The second LO 636b can also be configured to transmit the second carrier signal to the third mixer 680c.

[0289] The third mixer 680c can be configured to receive an encoded input signal from the modulation block 644a, receive a second carrier signal from the second LO 636b, upconvert the encoded input signal using the second carrier signal to generate a first modulated signal, wherein the first modulated signal is encoded with client data and has a predetermined frequency (i.e., BB frequency) of the second carrier signal, and send the first modulated signal to the fifth amplifier 684e.

[0290] The fifth amplifier 684e can be configured to receive a first modulation signal from the third mixer 680c, adjust the amplitude of the first modulation signal so that the amplified first modulation signal can drive the first mixer 680a, and send the amplified first modulation signal to the first mixer 680a.

[0291] The third amplifier 684c can be configured to receive a first carrier signal from the signal distribution block 698, adjust the amplitude of the first carrier signal to generate an amplified carrier signal that can drive the first mixer 680a, and send the amplified carrier signal to the first mixer 680a.

[0292] The first mixer 680a may be configured to receive an amplified carrier signal from the third amplifier 684c, an amplified first modulation signal from the fifth amplifier 684e, upconvert the amplified first modulation signal using the amplified carrier signal to generate a second modulation signal, wherein the second modulation signal is encoded with data and has a predetermined frequency of the amplified carrier signal (i.e., within the THz band 104, or in some specific embodiments, within the range of 300 GHz and 10 THz), and send the second modulation signal to the first amplifier 684a.

[0293] The first amplifier 684a can be configured to receive a second modulation signal from the first mixer 680a, adjust the amplitude of the second modulation signal so that the amplified second modulation signal can be transmitted through the first RF interface 664a, and send the amplified second modulation signal to the first RF interface 664a.

[0294] The first RF interface 664a can be configured to receive an amplified second modulated signal from the first amplifier 684a and transmit the amplified second modulated signal as an antenna feed signal 612a (i.e., where data is encoded) having a frequency within a predetermined frequency range (e.g., THz band 104, or in some embodiments, between 300 GHz and 10 THz). In some embodiments, the first RF interface 664a can be connected to one of the antennas 616 and configured to transmit the antenna feed signal 612a to the antenna 616. However, in other embodiments, one of the antennas 616 may be included instead of the first RF interface 664a.

[0295] Referring now to receiver circuitry 608b, a second RF interface 664b may be configured to receive an antenna output signal 612b (i.e., encoded with client data) within a predetermined frequency range (e.g., THz band 104, or in some specific embodiments, between 300 GHz and 10 THz), and to transmit the antenna output signal 612b to a second amplifier 684b. As described further in detail below, the second RF interface 664b may be configured to receive the antenna output signal 612b from one of antennas 616. However, in other embodiments, one of antennas 616 may be included instead of the second RF interface 664b.

[0296] The second amplifier 684b can be configured to receive the antenna output signal 612b from the second RF interface 664b, adjust the amplitude of the antenna output signal 612b to generate an amplified second transmission signal that can drive the second mixer 680b, and send the amplified second transmission signal to the second mixer 680b.

[0297] The fourth amplifier 684d can be configured to receive a first carrier signal from the signal distribution block 698, adjust the amplitude of the first carrier signal to generate an amplified carrier signal that can drive the second mixer 680b, and send the amplified carrier signal to the second mixer 680b.

[0298] The second mixer 680b can be configured to receive an amplified second transmission signal from the second amplifier 684b, receive an amplified carrier signal from the fourth amplifier 684d, downconvert the amplified second transmission signal using the amplified carrier signal to generate a third modulation signal in which data is encoded and has an IF or BB frequency, and send the third modulation signal to the sixth amplifier 684f.

[0299] The sixth amplifier 684f can be configured to receive a third modulation signal from the second mixer 680b, adjust the amplitude of the third modulation signal so that the amplified third modulation signal can drive the fourth mixer 680d, and send the amplified third modulation signal to the fourth mixer 680d.

[0300] The third LO 636c can be configured to generate a reference signal of a continuous waveform (e.g., a sine wave) having a predetermined frequency (i.e., the BB frequency). In some embodiments, the predetermined frequency (i.e., the BB frequency) of the reference signal is in the range of 8 GHz and 10 GHz. The third LO 636c can also be configured to send the reference signal to the fourth mixer 680d.

[0301] The fourth mixer 680d can be configured to receive an amplified third modulation signal from the sixth amplifier 684f, receive a reference signal from the third LO 636c, downconvert the amplified third modulation signal using the reference signal to generate an encoded output signal in which client data is encoded and has a predetermined frequency (i.e., BB frequency) of the reference signal, and send the encoded output signal to the modulation block 644a.

[0302] The client-side output 600b can be configured to transmit a second baseband signal 604b, in which client data is encoded, to one or more external components (e.g., control module 224). In some embodiments, the client-side output 600b is a pair of output interfaces. In some such embodiments, the client-side output 600b is an LVDS link configured to transmit LVDS signals, and the second baseband signal 604b is an LVDS signal in which client data is encoded.

[0303] Now for reference Figure 7 The illustration shows a schematic diagram of an exemplary embodiment of a folded modulator 700 constructed according to the present disclosure. The folded modulator 700 can be configured to perform wideband direct modulation to generate an coded signal and minimize distortion in doing so. The folded modulator 700 can employ a cascaded architecture (e.g., a “stacked” or “folded” cascaded circuit driver) to produce a linear or near-linear modulated output (i.e., the coded signal). In embodiments where the folded modulator 700 employs a cascaded architecture, the stack size can be proportional to the bandwidth.

[0304] Now for reference Figure 8 The diagram illustrates an exemplary embodiment of a rectifier detector 800 constructed according to the present disclosure. The rectifier detector 800 may be configured to perform direct detection of an incoming signal (i.e., an encoded signal). The rectifier detector 800 may be further configured to detect the envelope of the encoded signal or one or more amplitude transitions of the encoded signal to generate an output signal.

[0305] Now for reference Figure 9A The illustration shows a side view of an exemplary embodiment of an antenna 900 coupled to a fifth hollow waveguide 208e, constructed according to the present disclosure. However, it should be understood that the description of any particular antenna in reference antennas 416, 516, 616, and 900 can be referenced to any of the antennas 416, 516, 616, and 900 described herein. Figure 8 As shown in Figure A, antenna 900 typically includes a ground plane 904, a radiator 908 mounted on the ground plane 904, and a coaxial feed line 912 electrically connected to the radiator 908. In some embodiments, antenna 900 may lack the ground plane 904. In some embodiments, antenna 900 also includes a housing (not shown) surrounding the radiator 908. Antenna 900 can be a vertical antenna (i.e., an antenna extending orthogonally from the substrate) or a horizontal antenna (i.e., an antenna extending laterally from the substrate).

[0306] Radiator 908 can be configured to transmit and detect a radiation signal configured for coherent detection. In the illustrated embodiment, radiator 908 is a spiral radiator configured to transmit and detect a circularly polarized radiation signal. In this embodiment, radiator 908 has a length l radiator Diameter d radiator The spacing s between adjacent turns of radiator 908 radiator The radiator 908 is preferably positioned at a distance d from the fifth hollow waveguide 208e. gap Place.

[0307] Radiator 908 can be wound in a predetermined direction, such as clockwise (i.e., left-handed) or counterclockwise (i.e., right-handed). Although the radiator 908 of antenna 900 is... Figure 9A The antenna 900 is depicted as having a right-handed or counter-clockwise rotation direction, but it should be understood that the radiator 908 of the antenna 900 may be configured to have a left-handed or clockwise rotation direction.

[0308] In some embodiments, the signal for transmission can be sent to the antenna 900 via the coaxial feed 912. In other embodiments, the received RF signal can be sent from the antenna 900 via the coaxial feed 912.

[0309] In some embodiments, the length of the radiator 908 is l radiator It can be proportional to the wavelength of the signal being transmitted and / or received. In some embodiments, the length of the radiator 908 is l radiator The diameter d of the radiator 908 is in the range of 10 micrometers to 10 millimeters. In some embodiments, the diameter d of the radiator 908 is... radiator It can be proportional to the wavelength of the transmitted and / or received signal. In some embodiments, the diameter d of the radiator 908 radiator Within the range of 10 micrometers and 10 millimeters. In some embodiments, the spacing s between adjacent turns of the radiator 908 is... radiator It can be within the range of 1 micrometer and 1 millimeter.

[0310] The predetermined distance d between antenna 900 and hollow waveguide 208 gap The frequency can vary depending on the carrier frequency of the RF signal emitted by the antenna 900. In some embodiments, the antenna 900 is spaced from the hollow waveguide 208 by a predetermined distance d. gap Within the range of 3 μm and 3 mm. In one embodiment, the antenna 900 is spaced from the hollow waveguide 208 by a predetermined distance d. gap The diameter is 1 mm. In some embodiments, the antenna 900 can be directly connected to the fifth hollow waveguide 208e.

[0311] Now for reference Figure 9B The diagram shows a top view of another exemplary embodiment of an antenna 900 coupled to a fifth hollow waveguide 208e, constructed according to the present disclosure. The antenna 900 is similar in construction and function to the antenna 900, except that the antenna 900 includes a first radiator 908a formed of a conductive material having a plurality of coplanar windings. In one embodiment, the first radiator 908a is in a helical form. The first radiator 908a can be wound in a predetermined direction, such as clockwise (i.e., left-handed) or counterclockwise (i.e., right-handed). Although the first radiator 908a of the antenna 900 is in... Figure 9B The antenna 900 is depicted as having a right-handed or counter-clockwise rotation direction, but it should be understood that the first radiator 908a of the antenna 900 can be provided with a left-handed or clockwise rotation direction.

[0312] Other embodiments of antenna 900 include those as a gain horn antenna, a Cassegrain antenna, an omnidirectional antenna, a horn lens antenna, a point-focusing antenna, a waveguide probe antenna, a scalar-fed horn antenna, a wide-angle scalar-fed horn antenna, a triangular antenna, and a conical horn antenna.

[0313] Now for reference Figure 10 Another exemplary implementation of antenna 900 is shown therein. Figure 10 As shown, antenna 900 can be implemented as a dual-helix antenna. The dual-helix antenna 900 typically includes a ground plane 904a having a first differential pad 1100a and a second differential pad 1100b, and a second radiator 908b mounted on the ground plane 904a. In some embodiments, the dual-helix antenna 900 may lack the ground plane 904a. The second radiator 908b is typically in a double-helix shape and may have a first feed point 1104a electrically connected to the first differential pad 1100a and a second feed point 1104b electrically connected to the second differential pad 1100b. The first coaxial feed 1108a and the second coaxial feed 1108b may be electrically connected to the first differential pad 1100a and the second differential pad 1100b, respectively.

[0314] In some embodiments, the second radiator 908b can be configured to transmit and detect differential radiated signals. That is, in the transmission direction, the second radiator 908b can receive a first complementary antenna feed signal from a first feed point 1104a and a second complementary antenna feed signal from a second feed point 1104b, and transmit radiated signals based on the first and second complementary antenna feed signals. Furthermore, in the reception direction, the second radiator 908b can receive radiated signals and provide a first complementary antenna output signal to the first feed point 1104a and a second complementary antenna output signal to the second feed point 1104b. In such embodiments, the amplitudes of the first and second complementary antenna output signals can be equal but opposite in phase (i.e., 180° out of phase).

[0315] The second radiator 908b can be wound in a predetermined direction, such as clockwise or counterclockwise. Although the second radiator 908b of the dual-wire helical antenna 900 is depicted in Figure 9 as having a left-handed or clockwise rotation direction, it should be understood that the second radiator 908b of the dual-wire helical antenna 900 can be provided with a right-handed or counterclockwise rotation direction.

[0316] The second radiator 908b may include a first radiator portion 1112 and a second radiator portion 1114. The first radiator portion 1112 has a first end formed by a first feed point 1104a and a second end 1116 spaced apart from the first feed point 1104a. The first radiator portion 1112 is helical in shape. The second radiator portion 1114 has a third end formed by a second feed point 1104b and a fourth end 1118 spaced apart from the second feed point 1104b. The second radiator portion 1114 is helical in shape. The second end 1116 of the first radiator portion 1112 is connected to the fourth end 1118 of the second radiator portion 1114.

[0317] Now for reference Figure 11 and 12 , which shows Figure 10 Another exemplary embodiment of the dual-wire spiral antenna 900 shown. For example... Figure 11 and 12 As shown, in some embodiments, a conductive cone 1200 can be arranged around the dual-helix antenna 900 (i.e., the dual-helix antenna 900 is enclosed within the conductive cone 1200). The second radiator 908b can be wound in a predetermined direction, such as clockwise or counterclockwise. Although in Figure 11 and 12The second radiator 908b of the double-wire spiral antenna 900 enclosed within the conductive cone 1200 is depicted as having a left-handed or clockwise rotation direction. However, it should be understood that the second radiator 908b of the double-wire spiral antenna 900 enclosed within the conductive cone 1200 may be configured to have a right-handed or counterclockwise rotation direction.

[0318] The conductive cone 1200 may have a first end 1204a, a second end 1204b opposite to the first end 1204a, and a sidewall 1208 extending between the first end 1204a and the second end 1204b. The sidewall 1208 may define a first opening 1212a at the first end 1204a and a second opening 1212b at the second end 1204b. Figure 11 and 12 As shown, the first end 1204a of the conductive cone 1200 is typically provided with a diameter d4 that is shorter than the diameter d5 of the second end 1204b of the conductive cone 1200.

[0319] The dual-wire helical antenna 900, enclosed within a conductive cone 1200, can be configured to transmit circularly polarized signals with relatively high gain (e.g., greater than 6 dBi relative to isotropic gain, such as 10 dBi, 12 dBi, 14 dBi, 15 dBi, 16 dBi, 18 dBi, or 20 dBi). Figure 11 and 12 In the illustrated embodiment, the double-helix antenna 900 enclosed within the conductive cone 1200 can be used as an effective wideband polarizer. That is, the double-helix antenna 900 enclosed within the conductive cone 1200 can be configured to transmit circularly polarized RF signals with high radiation efficiency (e.g., greater than 50%, such as 60%, 70%, 75%, 80%, 85%, 90%, or 95%). Loss of radiation efficiency is typically due to losses in the conductor or substrate. Furthermore, the double-helix antenna 900 enclosed within the conductive cone 1200 can be configured to transmit circularly polarized signals with a wide bandwidth (e.g., greater than 10% of the center frequency, such as 12%, 14%, 15%, 16%, 18%, 20%, 22%, 24%, or 25%).

[0320] The diameter of the double-helix antenna 900 can be smaller than the wavelength of the signal emitted by the double-helix antenna 900. In some embodiments, the conductive cone 1200 can be made of a conductive material, such as aluminum, copper, silver, gold, other conductive metals, or combinations thereof.

[0321] Those skilled in the art will understand that a circularly polarized signal transmitted by the radiator 908 of the first specific antenna in antenna 900 can be received only by the radiator 908 of the second specific antenna in antenna 900, which has the same direction of rotation. That is, for example, Figure 8 Radiator 908 shown in A and Figure 8 The first radiator 908a shown in B is depicted as having a right-handed or counter-clockwise rotation direction. As a result, by Figure 9A The radiator 908 shown Figure 9B The circularly polarized RF signal transmitted by the first radiator 908a shown will have right-hand circular polarization (RHCP). On the other hand, Figure 10-12 The second radiator 908b shown is depicted as having a left-handed or clockwise rotation direction. As a result, by Figure 10-12 The circularly polarized RF signal transmitted by the second radiator 908b shown will have left-hand circular polarization (LHCP).

[0322] Because the circularly polarized signal transmitted by the radiator 908 of the first specific antenna in antenna 900 can be received only by the radiator 908 of the second specific antenna in antenna 900, which has the same direction of rotation, therefore... Figure 9A The radiator 908 shown or as Figure 9B The circularly polarized RF signal (i.e., the RHCP RF signal) emitted by the first radiator 908a shown cannot be generated by, as Figure 10-12 The second radiator 908b shown is a receiver. Similarly, as... Figure 9A The radiator 908 shown or as Figure 9B The first radiator 908a shown cannot receive signals from... Figure 10-12 The second radiator 908b shown transmits a circularly polarized signal (i.e., an LHCP RF signal). However, as... Figure 8 The circularly polarized signal (i.e., the RHCP RF signal) emitted by the radiator 908 shown in Figure A can be generated by, for example... Figure 9B The first radiator 908a shown receives, and is received by, as... Figure 10 The circularly polarized signal (i.e., the LHCP RF signal) emitted by the second radiator 908b shown can be generated by, for example... Figure 11 and 12 The second radiator 908b shown is a receiver.

[0323] Now for reference Figure 13 The diagram shows the enclosure Figure 11 and 12 A schematic diagram of the electric field 1300 generated by the double-wire helical antenna 900 within the conductive cone 1200. (See diagram for reference.) Figure 13 As shown, the double-helix antenna 900 enclosed within the conductive cone 1200 is operable to generate an electric field 1300, such that the near-field and far-field regions of the electric field 1300 are established to have greater directivity than that provided by a conventional antenna. Furthermore, the double-helix antenna 900 enclosed within the conductive cone 1200 is operable to generate the electric field 1300 in a manner that does not interfere with the circular polarization of the circularly polarized radiation signal transmitted by the second radiator 908b.

[0324] Now for reference Figure 14 The text appears to be a fragmented collection of characters and symbols, possibly from different sources. A direct translation isn't possible without further context or Figure 11 and 12 A schematic diagram of the radiation pattern 1400 of the dual-wire helical antenna 900 within the conductive cone 1200 is shown. The radiation pattern 1400 can correspond to a transmitted signal with a frequency of 2,000 GHz and a phase of 0°. (As shown...) Figure 14 As shown, the first curve 1404 illustrates the LHCP gain of the two-wire helical antenna 900 enclosed within the conductive cone 1200, while the second curve 1408 illustrates the overall directivity of the two-wire helical antenna 900 enclosed within the conductive cone 1200. The difference between the first curve 1404 and the second curve 1408 can indicate metallic and polarization losses. Figure 14 As shown and as above regarding Figure 13 As described, the dual-wire spiral antenna 900 enclosed within the conductive cone 1200 is operable to generate an electric field 1300 such that the near-field region 1304 and the far-field region 1308 of the electric field 1300 are established to have a greater directivity than that provided by a conventional antenna.

[0325] Now for reference Figure 15 and 16 The illustration shows a side view of an exemplary embodiment of a non-uniform double-helix antenna 1500 (hereinafter referred to as "non-uniform antenna 1500") constructed according to the present disclosure. Providing an antenna with a non-uniform design is effective because the dimensions of the helix determine the operating frequency. By changing the characteristic dimensions of the helix, a wider frequency band can be effectively radiated.

[0326] Similar to the dual-helix antenna 900 described above, the non-uniform antenna 1500 may include a ground plane 904a having a first differential pad 1100a and a second differential pad 1100b, and a non-uniform third radiator 908c mounted on the ground plane 904a. The third radiator 908c may have a plurality of turns 1504a-n, including at least a first turn 1504a and a second turn 1504b. For clarity, only the first turn 1504a and the second turn 1504b are labeled with reference numerals. The first turn 1504a may have a first characteristic dimension, while the second turn 1504b may have a second characteristic dimension different from the first characteristic dimension. The first turn 1504a may be adjacent to the second turn 1504b or not adjacent to the second turn 1504b (i.e., spaced apart).

[0327] exist Figure 15 In the embodiment shown, the first turn 1504a has a first spacing. The second turn 1504b has a second spacing. And the first spacing Smaller than the second spacing For example, in Figure 15 In the embodiment shown, the first turn 1504a has a first spacing. The second turn 1504b has a second spacing. And the first spacing Greater than the second spacing .

[0328] In some implementations, the non-uniform antenna 1500 may lack a ground plane 904a. The third radiator 908c is typically double-helix shaped and may have a first feed point 1104a electrically connected to the first differential pad 1100a and a second feed point 1104b electrically connected to the second differential pad 1100b. The first coaxial feed 1108a and the second coaxial feed 1108b may be electrically connected to the first differential pad 1100a and the second differential pad 1100b, respectively.

[0329] In some embodiments, the third radiator 908c can be configured to transmit and receive differential signals. That is, in the transmission direction, the third radiator 908c can receive a first complementary signal from the first feed point 1104a and a second complementary signal from the second feed point 1104b, and reflect the transmitted signal. Furthermore, in the reception direction, the third radiator 908c can receive the transmitted signal and provide the first complementary signal to the first feed point 1104a and the second complementary signal to the second feed point 1104b. In such embodiments, the amplitudes of the first and second complementary signals can be equal but their phases opposite (i.e., a phase difference of 180°).

[0330] The third radiator 908c can be wound in a predetermined direction, such as clockwise or counterclockwise. Although the third radiator 908c of the non-uniform antenna 1500... Figure 15 and 16 The antenna is described as having a right-handed or counter-clockwise rotation direction, but it should be understood that the third radiator 908c of the non-uniform antenna 1500 can be configured with a left-handed or clockwise rotation direction.

[0331] The third radiator 908c may include a first radiator portion 1112 and a second radiator portion 1114. The first radiator portion 1112 has a first end formed by a first feed point 1104a and a second end 1116 spaced apart from the first feed point 1104a. The first radiator portion 1112 is helical in form (i.e., spiral-shaped). The second radiator portion 1114 has a third end formed by a second feed point 1104b and a fourth end 1118 spaced apart from the second feed point 1104b. The second radiator portion 1114 is helical in form (i.e., spiral-shaped). Although the second end 1116 and the fourth end 1118 are shown disconnected from each other, it should be understood that in some embodiments, the second end 1116 of the first radiator portion 1112 is connected to the fourth end 1118 of the second radiator portion 1114.

[0332] Compared to existing uniform antennas and the uniform twin-helix antenna discussed herein, the non-uniform antenna 1500 provides a wider frequency response. The mathematical equations for the helical shape of the non-uniform radiator 908c of the non-uniform antenna 1500 in three-dimensional space are shown in Table 1 below. Figure 17 The curves shown in Figure 1700 illustrate the polarization decoupling of the uniform antenna in the frequency range between 0.80 THz and 1.40 THz. Figure 18 The curve shown is illustrated in graph 1800. (As shown...) Figure 17 and 18 As shown, polarization decoupling can be determined by subtracting the left-hand circular polarization directionality (i.e., DirLHCP) from the right-hand circular polarization directionality (i.e., DirRHCP). See Table 1 and... Figure 16 As shown, the right-hand circular polarization directivity (i.e., DirRHCP) of the non-uniform antenna 1500 can be relatively constant (i.e., 11.5 dBi ± 1 dBi) in the frequency range between 0.80 THz and 1.40 THz. Furthermore, as... Figure 17 As shown, the polarization decoupling (i.e., DirRHCP - DirLHCP) of the non-uniform antenna 1500 remains above 25 dB in the frequency range between 0.80 THz and 1.40 THz. Conversely, as Figure 18 As shown, the polarization decoupling of the uniform antenna (i.e., DirRHCP - DirLHCP) drops below 25 dB at the edge of the frequency band and slightly below 25 dB in the mid-frequency band.

[0333] Table 1. Mathematical equations for the spiral shape of the non-uniform radiator 908c in three-dimensional space of the non-uniform antenna 1500.

[0334] Now for reference Figure 18 and20 , which shows Figure 15 and 16 A side view of a further exemplary embodiment of the non-uniform antenna 1500 shown. For clarity, the differential pad 1100 and feed point 1104 are... Figure 18 and 19 There are no accompanying diagrams labeled in the text. Figure 19 and 20 In the embodiment shown, the first feature dimension and the second feature dimension are not the spacing, but the diameter. Figure 19 In the embodiment shown, the first turn 1504a has a first diameter The second turn 1504b has a second diameter And the first diameter Smaller than the second diameter .exist Figure 20 In the embodiment shown, the first turn 1504a has a first diameter The second turn 1504b has a second diameter And the first diameter Larger than the second diameter .

[0335] Change the diameter of turn 1504 of the third radiator 908c. Instead of the 1504-turn spacing of the third radiator 908c Different frequency bands or different ground plane dimensions, conductor dimensions, etc., may be advantageous.

[0336] It should be understood that a third radiator 908c and / or a non-uniform antenna 1500 may be included in place of any of the corresponding radiators 908 and / or antennas 900 described herein. Furthermore, it should be understood that although the second turn 1504b is shown as being directly adjacent to the first turn 1504a, one or more turns may exist between the first turn 1504a and the second turn 1504b. Finally, it should be understood that although the first turn 1504a is shown as being directly adjacent to the ground plane 904a, one or more turns may exist between the ground plane 904a and the first turn 1504a.

[0337] Now for reference Figure 21 Images 22 A-22C illustrate a differential waveguide probe antenna 2100 constructed according to this disclosure. The differential waveguide probe antenna 2100 is configured to generate and transmit a transmitted signal. Conversely, the differential waveguide probe antenna 2100 is also configured to receive a transmitted signal. The differential waveguide probe antenna 2100 includes a pair of waveguide probes 2104, which includes a first waveguide probe 2104a and a second waveguide probe 2104b.

[0338] In some embodiments, the differential waveguide probe antenna 2100 may further include an intermediate waveguide 2108 configured to propagate a transmitted signal. In such embodiments, the differential waveguide probe antenna 2100 may also be configured to generate a transmitted signal and transmit it into the intermediate waveguide 2108. Conversely, in such embodiments, the differential waveguide probe antenna 2100 may also be configured to receive a transmitted signal from the intermediate waveguide 2108.

[0339] The intermediate waveguide 2108 may have a first end 2112a, a second end 2112b opposite to the first end 2112a (the first end 2112a and the second end 2112b are collectively referred to as "end 2112"), and a surface 2116 extending between the ends 2112. In some embodiments, a back reflector 2118 may be adjacent to the first end 2112a. The surface 2116 may be made of metal and may have a diameter of two wavelengths of the transmitted signal at less than 10 THz (or the maximum frequency in the frequency band occupied by the transmission network 200). (i.e., 60 μm), and half-wavelength (i.e., 0.5 mm) at times greater than 300 GHz (or the smallest frequency in the band occupied by transmission network 200). The intermediate waveguide 2108 can be constructed to ensure the establishment of one or more desired waveguide modes. That is, if the intermediate waveguide 2108 is constructed with a smaller size, one or more desired waveguide modes may fail to propagate, and if the intermediate waveguide 2108 is constructed with a larger size, one or more undesired waveguide modes may be excited. In some embodiments, one or more desired waveguide modes of the intermediate waveguide 2108 are sufficiently matched with one or more desired waveguide modes of the hollow waveguide 208, such that coupling loss between the intermediate waveguide 2108 and the hollow waveguide 208 is minimized (e.g., coupling loss is in the range of 0.1 dB to 5.0 dB).

[0340] Waveguide probes 2104 can be positioned on opposite sides of the surface 2116 of the intermediate waveguide 2108 and can extend toward each other into the intermediate waveguide 2108, but can be spaced apart from each other. Waveguide probes 2104 can thus establish a strong electric field consistent with one or more desired waveguide modes. Each waveguide probe 2104 can be excited with a transmitted signal. In some embodiments, each waveguide probe 2104 can be excited with a transmitted signal of equal strength and / or opposite phase. That is, waveguide probes 2104 can be configured to receive the transmitted signal as a differential signal having a first complementary signal and a second complementary signal, and generate and transmit the transmitted signal in the form of electromagnetic waves. Conversely, waveguide probes 2104 can also be configured to receive and provide the transmitted signal as a differential signal having a first complementary signal and a second complementary signal.

[0341] In some embodiments, the intermediate waveguide 2108 may have a flared end at the second end 2112b, configured to facilitate mode switching between the intermediate waveguide 2108 and the hollow waveguide 208. In such an embodiment, the surface 2116 at the flared end may have a diameter greater than the diameter of the flared end. diameter In some such embodiments, the flared end can be integrally formed with the intermediate waveguide 2108. However, in other such embodiments, the flared end can be configured as a horn 2120 separate from but coupled to the intermediate waveguide 2108. The horn 2120 may have a first end 2124a adjacent to the second end 2112b of the intermediate waveguide 2108, a second end 2124b opposite to the first end 2124a (the first end 2124a and the second end 2124b are collectively referred to as "end 2124"), and a curved surface 2128 extending between the ends 2124. The curved surface 2128 at the first end 2124a may have a diameter equal to the diameter of the first end 2124a. diameter The differential waveguide probe antenna 2100 can be configured to transmit a signal with a wide (i.e., greater than 50%) bandwidth into the hollow waveguide 208, at least in part because the energy contribution from each waveguide probe 2104 effectively cancels out the higher-order, unintended waveguide modes of the other waveguide probe 2104. Figure 22D The curve 2500 shown illustrates the polarization decoupling of the differential waveguide probe antenna 2100 in the frequency range between 0.60 THz and 1.80 THz.

[0342] Now for reference Figure 23 , 24A 24B, which illustrates an exemplary embodiment of a differential conical antenna 2600 constructed according to the present disclosure. The differential conical antenna 2600 is configured to generate and transmit transmitted signals in the form of electromagnetic waves, and conversely, to receive transmitted signals in the form of electromagnetic waves, and includes a pair of conductors, the pair including a first conductor 2604a and a distance spaced from the first conductor 2604a. The second conductor 2604b (collectively referred to as “Conductor 2604”).

[0343] The differential conical antenna 2600 can resemble a conical slot antenna in some respects and a ridged horn antenna in others. However, the differential conical antenna 2600 differs from such antennas because it has differential transmission and is coupled into a hollow waveguide 208, allowing the transmitted signal to have multiple waveguide modes.

[0344] exist Figure 23 , 24AIn the embodiment shown in 24B, the intermediate waveguide 2108 has a first planar, longitudinally oriented curved surface 2608a and a second planar, longitudinally oriented curved surface 2608b (collectively referred to as "curved surface 2608") adjacent to the space 2612. Figure 23 , 24A In the embodiment shown in 24B, conductors 2604 collectively define the curved surface 2608 of the intermediate waveguide 2108 and form a space 2612 between the conductors 2604. As described above, the intermediate waveguide 2108 is configured to propagate a transmitted signal in the form of an electromagnetic wave. In such an embodiment, the differential conical antenna 2600 may also be configured to generate and transmit a transmitted signal into the intermediate waveguide 2108, and to receive a transmitted signal from the intermediate waveguide 2108.

[0345] In some embodiments, the distance between the first conductor 2604a and the second conductor 2604b at the first end 2112a of the intermediate waveguide 2108 Two wavelengths of the transmitted signal at frequencies less than 10 THz (or the highest frequency in the frequency band occupied by transmission network 200), and half the wavelength at frequencies greater than 300 GHz (or the lowest frequency in the frequency band occupied by transmission network 200). Distance can be selected. A single waveguide mode is established for the frequency of the transmitted signal. In some embodiments, the distance between conductors 2604 at the second end 2112b of the intermediate waveguide 2108 is... Greater than distance The tapered shape allows for the creation of continuously scaling geometries that achieve an ultrawide (i.e., greater than 50%) bandwidth. As energy is emitted along conductor 2604, one or more desired waveguide modes are established between conductors 2604 and subsequently emitted into intermediate waveguide 2108.

[0346] In some embodiments, each conductor 2604 may be fed with transmission signals of equal strength and / or opposite phase. That is, conductor 2604 may be configured to receive transmission signals as differential signals having a first complementary signal and a second complementary signal, and to generate and transmit transmission signals in the form of electromagnetic waves. Conversely, conductor 2604 may also be configured to receive transmission signals and provide transmission signals as differential signals having a first complementary signal and a second complementary signal.

[0347] The thickness and width of the transmission line at the feed point can be selected to establish a characteristic impedance that matches the receiver and / or driver. Those skilled in the art will understand how to perform such calculations. Figure 24B As shown, the differential conical antenna 2600 may also include one or more ground connections, such as a first ground connection 2800a and a second ground connection 2800b. Figure 24CThe curve 2900 shown illustrates the polarization decoupling of the differential conical antenna 2600 in the frequency range between 0.50 THz and 2.00 THz.

[0348] Now for reference Figure 25 The illustration shows an exemplary embodiment of a differential microstrip patch antenna 3000 constructed according to the present disclosure. The differential microstrip patch antenna 3000 is configured to generate and transmit transmission signals in the form of electromagnetic waves, and conversely, to receive transmission signals in the form of electromagnetic waves. It includes a pair of microstrip patch antennas, the pair comprising a first microstrip patch antenna 3004a and a spaced distance from the first microstrip patch antenna 3004a. The second microstrip patch antenna 3004b (collectively referred to as "microstrip patch antenna 3004").

[0349] In some embodiments, the differential microstrip patch antenna 3000 may further include a horn 2120 having a first end 2124a near the microstrip patch antenna 3004, a second end 2124b away from the microstrip patch antenna 3004, and a curved surface 2128 extending between the ends 2124. The curved surface 2128 at the first end 2124a may have a diameter Furthermore, the curved surface 2028 at the second end 2124b can have a diameter greater than that of the other end. diameter .

[0350] In some embodiments, each of the microstrip patch antennas 3004 can be fed with transmission signals of equal strength and / or opposite phase. That is, the microstrip patch antenna 3004 can be configured to receive a transmission signal as a differential signal having a first complementary signal and a second complementary signal, and to generate and transmit a transmission signal in the form of electromagnetic waves. Conversely, the microstrip patch antenna 3004 can also be configured to receive and provide a transmission signal as a differential signal having a first complementary signal and a second complementary signal.

[0351] The differential waveguide probe antenna 2100, the differential conical antenna 2600, and the differential microstrip patch antenna 3000 are configured to generate a transmitted signal in a linear polarization form.

[0352] Now for reference Figure 2627 A-27C, which illustrate schematic diagrams of exemplary embodiments of a single-ended waveguide probe antenna 3008 constructed according to the present disclosure. In some embodiments, the single-ended waveguide probe antenna 3008 may omit the second waveguide probe 2104b, thus including only the first waveguide probe 2104a. Furthermore, in some embodiments, the surface 2116 of the intermediate waveguide 2108 may define an opening 3012 through which the first waveguide probe 2104a extends. As described above, in some embodiments, the first end 2112a of the intermediate waveguide 2108 may serve as a back reflector.

[0353] Now for reference Figure 28 , 29A -29C and 30A-30C, which illustrate schematic diagrams of exemplary embodiments of a slot antenna 5800 constructed according to the present disclosure. Figure 28 , 29A As shown in -29C and 30A-30C, the slot antenna 5800 may include a ground plane 904 disposed between an intermediate waveguide 2108 and a back reflector 2118. In some embodiments, the ground plane 904 may define one or more slots 3016 (e.g., in...). Figure 28 and 29A The first slot 3016a shown in -29C and in Figures 30A-30C The second slit 3016b shown in the figure (hereinafter, "slit 3016").

[0354] Now for reference Figure 31 The diagram illustrates an exemplary embodiment of a transmission network 3100 (hereinafter referred to as "network 3100") constructed according to the present disclosure. Network 3100 typically includes a first network element 3102a, a second network element 3102b, and a hollow waveguide 3104 communicatively coupled to the first network element 3102a and the second network element 3102b.

[0355] Although network 3100 is described herein as including a first network element 3102a for transmitting signals and a second network element 3102b for receiving such signals, it should be understood that network 3100 may be bidirectional; that is, network 3100 may also include a second network element 3102b for transmitting signals and a first network element 3102a for receiving such signals. Therefore, in some such embodiments, hollow waveguide 3104 may be bidirectional (i.e., configured to propagate signals simultaneously in both directions); however, in other such embodiments, hollow waveguide 3104 includes a first hollow waveguide (not shown) configured to propagate signals in a first direction (e.g., from the first network element 3102a to the second network element 3102b), and a second hollow waveguide (not shown) configured to propagate signals in a second direction opposite to the first direction (e.g., from the second network element 3102b to the first network element 3102a).

[0356] The first network element 3102a typically includes one or more transmitters 3106 (hereinafter referred to as "transmitter 3106" or collectively as "transmitter 3106") and a transmitter antenna array 3108. The transmitter 3106 may include a transmitter circuitry configured to generate multiple channel signals 3112 (such as the first channel signal 3112a and the second channel signal 3112b shown in FIG. 30). The transmitter antenna array 3108 may include multiple transmitter antennas 3116, such as the first transmitter antenna 3116a and the second transmitter antenna 3116b shown in FIG. 30.

[0357] Channel signal 3112 may have input data encoded in a modulation format and at a carrier frequency in the range of 300 GHz and 10 THz. That is, first channel signal 3112a and second channel signal 3112b may have first input data encoded in a first modulation format and at a first carrier frequency in the range of 300 GHz and 10 THz. First channel signal 3112a and second channel signal 3112b are preferably identical signals carrying the same data with the same modulation format and the same frequency, except that first channel signal 3112a and second channel signal 3112b may be phase-shifted relative to each other to change the polarization angle of the electromagnetic wave generated by transmitter antenna array 3108, as described below. Second channel signal 3112b may have second input data (e.g., the same as the first input data) encoded in a second modulation format and at a second carrier frequency in the range of 300 GHz and 10 THz.

[0358] Each modulation scheme described herein can be selected from the group consisting of: intensity modulation (IM) / direct detection (DD) (IM / DD); non-return-to-zero modulation (NRZ); pulse amplitude modulation-n (PAMn); IM-PAMn; m-quadrature amplitude modulation (mQAM); and single-sideband modulation (SSB). In an implementation where one or more modulation schemes are PAMn or IM-PAMn, n can be a power of 2 (e.g., 2, 4, 8, 16, 32, 64, etc.). Similarly, in an implementation where one or more modulation schemes are mQAM, m can be a power of 2 greater than or equal to 4 (e.g., 4, 8, 16, 32, 64, etc.).

[0359] In some embodiments, the first modulation format and the second modulation format are the same modulation format. In some embodiments, the first carrier frequency and the second carrier frequency have the same carrier frequency in the range of 300 GHz and 10 THz.

[0360] The first transmitter antenna 3116a and the second transmitter antenna 3116b of the transmitter antenna array 3108 can be configured to receive a channel signal 3112 and transmit a plurality of wireless signals 3120, such as the first wireless signal 3120a and the second wireless signal 3120b shown in FIG. 30. That is, the first transmitter antenna 3116a can be configured to receive a first channel signal 3112a having first input data encoded in a first modulation format and a first carrier frequency, and to transmit a first wireless signal 3120a having first input data encoded in a first modulation format and a first carrier frequency, while the second transmitter antenna 3116b can be configured to receive a second channel signal 3112b having second input data encoded in a second modulation format and a second carrier frequency, and to transmit a second wireless signal 3120b having second input data encoded in a second modulation format and a second carrier frequency.

[0361] The first transmitter antenna 3116a can be configured to direct a first circular polarization into the first wireless signal 3120a. In some embodiments, the first circular polarization is left-handed circular polarization (LHCP). However, in other embodiments, the first circular polarization can be right-handed circular polarization (RHCP). Similarly, the second transmitter antenna 3116b can be configured to direct a second circular polarization into the second wireless signal 3120b, wherein the second circular polarization is orthogonal to the first circular polarization. Therefore, in embodiments where the first circular polarization is LHCP, the second circular polarization is RHCP. However, in embodiments where the first circular polarization is RHCP, the second circular polarization is LHCP.

[0362] The first transmitter antenna 3116a and the second transmitter antenna 3116b are positioned adjacent to each other such that the first wireless signal 3120a and the second wireless signal 3120b interact to form a linearly polarized wireless signal 3124. In some embodiments, the linear polarization is horizontal linear polarization (HLP). In other embodiments, the linear polarization is vertical linear polarization (VLP). Those skilled in the art will understand that HLP or VLP can have a polarization angle such that the polarization is neither completely horizontal nor completely vertical.

[0363] It should be understood that circular polarization typically consists of linear polarization with a 90° phase shift, as shown in equations (1) and (2) below: (1) (2) Combining two orthogonal circular polarizations produces the first linear polarization, HLP in this example, as shown in equation (3) below: (3) Due to the law of conservation of energy, the j-th term is eliminated (i.e., and This does not result in energy loss. The linearly polarized wireless signal 3124, formed by multiple circularly polarized wireless signals, provides high broadband polarization diversity, likely due to the cancellation of polarization non-ideals of each individual antenna during operation.

[0364] Furthermore, after applying a 180° phase shift to one of the circular polarizations (RHCP in this example), combining the two orthogonal circular polarizations results in a second linear polarization orthogonal to the first linear polarization (VLP in this example), as shown in equation (4) below: (4) However, applying a 180° phase shift to one of the circular polarizations may result in a degraded quality of the excitation field.

[0365] Alternatively, after applying a 90° physical phase shift to each of the circular polarizations, combining two orthogonal circular polarizations—such as by physically rotating the first transmitter antenna 3116a and the second transmitter antenna 3116b—results in a third linear polarization orthogonal to the first linear polarization—VLP in this example—as shown in equation (5) below: (5) Finally, those skilled in the art will understand that applying a phase shift in the range between 0° and 180° to each circular polarization can result in polarization having a polarization angle such that the polarization is neither perfectly horizontal nor perfectly vertical.

[0366] The second network element 3102b typically includes a receiver antenna array 3128 and one or more receivers 3132 (hereinafter referred to as "receiver 3132", or collectively "receiver 3132"). The receiver antenna array 3128 may include a plurality of receiver antennas 3136, such as the first receiver antenna 3136a and the second receiver antenna 3136b shown in FIG. 30. The receiver 3132 may include a receiver circuitry configured to extract input data from the channel signal 3112. That is, the receiver circuitry may be configured to extract first input data from the first channel signal 3112a and second input data from the second channel signal 3112b, wherein, as described above, the second channel signal 3112b is preferably the same input data.

[0367] The first receiver antenna 3136a and the second receiver antenna 3136b of the receiver antenna array 3128 can be configured to receive the radio signal 3120 and generate the channel signal 3112. That is, the first receiver antenna 3136a can be configured to receive the first radio signal 3120a having first input data encoded in a first modulation format and a first carrier frequency, and generate the first channel signal 3112a having the first input data encoded in the first modulation format and the first carrier frequency, while the second receiver antenna 3136b can be configured to receive the second radio signal 3120b having second input data encoded in a second modulation format and a second carrier frequency, and generate the second channel signal 3112b having the second input data encoded in a second modulation format and a second carrier frequency.

[0368] The first receiver antenna 3136a can be configured to receive a wireless signal with a first circular polarization. Similarly, the second receiver antenna 3136b can be configured to receive a wireless signal with a second circular polarization.

[0369] Now for reference Figure 32A , which shows Figure 31 A schematic diagram of an exemplary embodiment of transmitter 3106 is shown. As described above, transmitter 3106 may include components configured to generate channel signal 3112 (such as...). Figure 32A The transmitter circuitry shown includes a first channel signal 3112a and a second channel signal 3112b. Therefore, the transmitter 3106 may include a plurality of channel signal generators 3200 configured to generate channel signals 3112, such as a first channel signal generator 3200a configured to generate the first channel signal 3112a and a transmitter 3200a configured to generate... Figure 32A The second channel signal generator 3200b shown is the second channel signal generator for the second channel signal 3112b.

[0370] Misalignment between transmitter antenna array 3108 and receiver antenna array 3128 exceeding a certain amount (e.g., 3.2°) may result in reduced power in the intended polarization. And the power increases in unexpected polarization. Where θ is the misalignment angle, resulting in a reduction in polarization diversity. To address this challenge, in some embodiments, transmitter 3106 may further include phase shift circuitry 3204, configured to induce a phase shift relative to the second channel signal 3112b in the first channel signal 3112a to induce a polarization angle in the linearly polarized radio signal 3124. Figure 31 As shown, in this specific embodiment, the phase shift circuit 3204 may also be configured to receive the polarization signal 3208 and, at least in part, induce a phase shift in the first channel signal 3112a relative to the second channel signal 3112b based on the polarization signal 3208. Inducing a phase shift in the first channel signal 3112a relative to the second channel signal 3112b, at least in part, based on the polarization signal 3208, can have the effect of aligning the transmitter antenna array 3108 of the first network element 3102a with the receiver antenna array 3128 of the second network element 3102b to maximize the received power at the receiver 3132.

[0371] Now for reference Figure 32B , which shows Figure 31 The diagram illustrates an exemplary embodiment of receiver 3132. As described above, the receiver circuitry can be configured to extract first input data from a first channel signal 3112a and second input data from a second channel signal 3112b. Therefore, receiver 3132 may include a plurality of channel signal generators 3212 configured to generate channel signals 3112, such as… Figure 32BThe first channel signal generator 3212a, configured to generate a first channel signal 3112a, and the second channel signal generator 3212b, configured to generate a second channel signal 3112b, are shown in the figure.

[0372] As described above, a misalignment of more than a certain amount (e.g., 3.2°) between the transmitter antenna array 3108 and the receiver antenna array 3128 may result in a reduction in power in the intended polarization. And the power increases in unexpected polarization. This leads to a reduction in polarization diversity. To address this challenge, in some embodiments, receiver 3132 may further include a polarization signal generator 3216 configured to generate a polarization signal 3208 based on the polarization angle between the first channel signal 3112a and the second channel signal 3112b. The polarization signal generator 3216 may include a power measurement circuitry for measuring the power of the first channel signal 3112a and the second channel signal 3112b.

[0373] To calibrate the polarization angle caused by the phase shift circuit 3204, a series of first channel signals 3112a and second channel signals 3112b, each having a known phase shift relative to the others, can be provided to the transmitter antenna array 3108 and subsequently received by the receiver antenna array 3128. The first channel signals 3112a and second channel signals 3112b are received by the receiver 3132 and, for example, analyzed by a polarization signal generator 3216 to generate a polarization signal 3208. The polarization signal generator 3216 may include: a receiver processor 3220 that executes logic operable to search for the strongest signal and use that information about the strongest signal to generate the polarization signal 3208; and a receiver communication unit 3224 that transmits the polarization signal 3208 to the phase shift circuit 3204, which may include a transmitter communication unit 3228 that receives the polarization signal 3208 from the polarization signal generator 3216. The polarization signal 3208 is correlated with a specific channel signal in a first channel signal 3112a and a second channel signal 3112b having a known phase shift, and can indicate the power received by the receiver 3132. The phase shift circuit 3204 may include a transmitter processor 3232 that executes logic operable to analyze the polarization signal 3208 and select the phase shift that delivers the maximum power to the receiver 3132 for the first channel signal 3112a and the second channel signal 3112b. The phase shift circuit 3204 then uses the selected phase shift to form the first channel signal 3112a and the second channel signal 3112b. This calibration process can be performed periodically, such as hourly, daily, etc.

[0374] Now for reference Figure 33 , which shows Figure 31The diagram illustrates an exemplary embodiment of the transmitter antenna array 3108. It should be understood that the receiver antenna array 3128 may be similar in construction and function to the transmitter antenna array 3108, except that the receiver antenna 3136 of the receiver antenna array 3128 may be wound in the opposite direction to its corresponding counterpart (i.e., the transmitter antenna 3116) of the transmitter antenna array 3108.

[0375] As described above, the transmitter antenna array 3108 may include a transmitter antenna 3116, which may include... Figure 33 The first transmitter antenna 3116a and the second transmitter antenna 3116b are shown. The transmitter antenna 3116 of the transmitter antenna array 3108 is... Figure 33 The diagram shows a 1×2 grid pattern.

[0376] In some embodiments, the distance between the first transmitter antenna 3116a and the second transmitter antenna 3116b d It can be equal to 1.5 times the wavelength λ. However, in other embodiments, the distance between the first transmitter antenna 3116a and the second transmitter antenna 3116b... d It can be a number greater than or less than 1.5 times the wavelength λ. For example, in some embodiments, the distance between the first transmitter antenna 3116a and the second transmitter antenna 3116b d It can be less than the wavelength λ. However, in other embodiments, the distance between the first transmitter antenna 3116a and the second transmitter antenna 3116b is... d It can be a multiple of the wavelength λ.

[0377] Now for reference Figure 34 The diagram illustrates another exemplary embodiment of a transmission network 3100a (hereinafter referred to as "network 3100a") constructed according to the present disclosure. Network 3100a typically includes a third network element 3102c, a fourth network element 3102d, and a hollow waveguide 3104 communicatively coupled to the third network element 3102c and the fourth network element 3102d.

[0378] and Figure 31 Unlike the first network element 3102a shown, the third network element 3102c typically includes multiple transmitters 3106, for example... Figure 34 The first transmitter 3106a and the second transmitter 3106b, as well as the transmitter antenna array 3108a, are shown. Similarly, with Figure 31 Unlike the second network element 3102b shown, the fourth network element 3102d typically includes a receiver antenna array 3128a and multiple receivers 3132, for example... Figure 34The first receiver 3132a and the second receiver 3132b are shown.

[0379] Transmitter antenna array 3108a can be similar to Figure 31 The transmitter antenna array 3108 shown includes a first transmitter antenna 3116a and a second transmitter antenna 3116b forming a first transmitter antenna pair, and also includes a third transmitter antenna 3116c and a fourth transmitter antenna 3116d forming a second transmitter antenna pair. Although the transmitter antenna array 3108a is described herein as including four transmitter antennas 3116, it should be understood that the transmitter antenna array 3108a may include a number of transmitter antennas 3116, whether greater or less than four.

[0380] The first transmitter 3106a can be similar to Figure 31 The transmitter 3106 shown in Figure 30 is a second transmitter 3106b, which may be similar to the transmitter 3106 shown in Figure 30, except that the channel signal 3112 transmitted by the second transmitter 3106b may include a third channel signal 3112c and a fourth channel signal 3112d.

[0381] As described above, channel signal 3112 may have input data encoded with a specific modulation format and a specific carrier frequency within the range of 300 GHz and 10 THz. That is, as described above, the first channel signal 3112a may have first input data encoded with a first modulation format and a first carrier frequency within the range of 300 GHz and 10 THz, and the second channel signal 3112b may have second input data encoded with a second modulation format and a second carrier frequency within the range of 300 GHz and 10 THz. Similarly, the third channel signal 3112c may have third input data encoded with a third modulation format and a third carrier frequency within the range of 300 GHz and 10 THz, and the fourth channel signal 3112d may have fourth input data encoded with a fourth modulation format and a fourth carrier frequency within the range of 300 GHz and 10 THz.

[0382] In some implementations, two or more of the first modulation format, second modulation format, third modulation format, and fourth modulation format are the same modulation format. For example, the first modulation format and the second modulation format can be the same modulation format. Furthermore, the third modulation format and the fourth modulation format can be the same modulation format.

[0383] In some embodiments, two or more of the first carrier frequency, second carrier frequency, third carrier frequency, and fourth carrier frequency are the same carrier frequency in the range of 300 GHz and 10 THz. For example, the first carrier frequency and the second carrier frequency may be the same carrier frequency; and the third carrier frequency and the fourth carrier frequency may be the same carrier frequency. In some embodiments, two or more of the first carrier frequency and the second carrier frequency may be different from the third carrier frequency and the fourth carrier frequency.

[0384] As described above, the transmitter antenna 3116 of the transmitter antenna array 3108a can be configured to receive channel signal 3112 and transmit wireless signals 3120, such as a first wireless signal 3120a, a second wireless signal 3120b, a third wireless signal 3120c, and a fourth wireless signal 3120d, as shown above. Figure 34 As shown. That is, the third transmitter antenna 3116c can be configured to receive a third channel signal 3112c having third input data encoded in a third modulation format and a third carrier frequency, and to transmit a third wireless signal 3120c having third input data encoded in a third modulation format and a third carrier frequency, and the fourth transmitter antenna 3116d can be configured to receive a fourth channel signal 3112d having fourth input data encoded in a fourth modulation format and a fourth carrier frequency, and to transmit a fourth wireless signal 3120d having fourth input data encoded in a fourth modulation format and a fourth carrier frequency.

[0385] As described above, the first transmitter antenna 3116a can be configured to guide a first circular polarization into the first wireless signal 3120a, and the second transmitter antenna 3116b can be configured to guide a second circular polarization into the second wireless signal 3120b, wherein the second circular polarization is orthogonal to the first circular polarization. Similarly, the third transmitter antenna 3116c can be configured to guide a third circular polarization into the third wireless signal 3120c, and the fourth transmitter antenna 3116d can be configured to guide a fourth circular polarization into the fourth wireless signal 3120d, wherein the fourth circular polarization is orthogonal to the third circular polarization.

[0386] The first wireless signal 3120a and the second wireless signal 3120b can interact to form a first linearly polarized wireless signal 3124a with a first linear polarization. Similarly, the third wireless signal 3120c and the fourth wireless signal 3120d can interact to form a second linearly polarized wireless signal 3124b with a second linear polarization, wherein the second linear polarization is orthogonal to the first linear polarization. The first linearly polarized wireless signal 3124a can be similar to the linearly polarized wireless signal 3124 shown in FIG. 30. Similarly, the second linearly polarized wireless signal 3124b can be similar to... Figure 31The linearly polarized wireless signal 3124 is shown.

[0387] In some embodiments, the first linearly polarized wireless signal 3124a has a first polarization angle, and the second linearly polarized wireless signal 3124b has a second polarization angle, wherein the first polarization angle and the second polarization angle are offset by a degree in the range between 86.8° and 93.2°.

[0388] Receiver antenna array 3128a can be similar to Figure 31 The receiver antenna array 3128 shown includes a first receiver antenna 3136a and a second receiver antenna 3136b forming a first receiver antenna pair, and further includes a third receiver antenna 3136c and a fourth receiver antenna 3136d forming a second receiver antenna pair. Although the receiver antenna array 3128a is described herein as comprising four receiver antennas 3136, it should be understood that the receiver antenna array 3128a may include an even number of receiver antennas 3136, whether greater than or less than four.

[0389] The first receiver 3132a can be similar to Figure 31 The receiver 3132 shown in FIG. 30 is similar to the receiver 3132 shown in FIG. 30, except that the channel signal 3112 received by the second receiver 3132b may include a third channel signal 3112c and a fourth channel signal 3112d.

[0390] As described above, receiver antenna 3136 of receiver antenna array 3128a can be configured to receive radio signal 3120 and generate channel signal 3112. That is, third receiver antenna 3136c can be configured to receive third radio signal 3120c having third input data encoded in a third modulation format and a third carrier frequency, and generate third channel signal 3112c having third input data encoded in a third modulation format and a third carrier frequency; and fourth receiver antenna 3136d can be configured to receive fourth radio signal 3120d having fourth input data encoded in a fourth modulation format and a fourth carrier frequency, and generate fourth channel signal 3112d having fourth input data encoded in a fourth modulation format and a fourth carrier frequency.

[0391] As described above, the first receiver antenna 3136a can be configured to receive a first wireless signal 3120a having first input data encoded in a first modulation format and a first carrier frequency, and generate a first channel signal 3112a having the first input data encoded in a first modulation format and a first carrier frequency, while the second receiver antenna 3136b can be configured to receive a second wireless signal 3120b having second input data encoded in a second modulation format and a second carrier frequency, and generate a second channel signal 3112b having the second input data encoded in a second modulation format and a second carrier frequency. Similarly, the third receiver antenna 3136c can be configured to receive a third radio signal 3120c having third input data encoded with a third modulation format and a third carrier frequency, and generate a third channel signal 3112c having third input data encoded with a third modulation format and a third carrier frequency, while the fourth receiver antenna 3136d can be configured to receive a fourth radio signal 3120d having fourth input data encoded with a fourth modulation format and a fourth carrier frequency, and generate a fourth channel signal 3112d having fourth input data encoded with a fourth modulation format and a fourth carrier frequency.

[0392] Now for reference Figure 35A , which shows Figure 34 The diagram illustrates an exemplary embodiment of the transmitter antenna array 3108a. It should be understood that the receiver antenna array 3128a can be similar to the transmitter antenna array 3108a, which includes a receiver antenna 3136 in the same direction as the transmitter antenna 3116. In some embodiments, the receiver antennas 3136 of the receiver antenna array 3128a may be wound in the opposite direction to their respective counterparts (i.e., the transmitter antennas 3116) of the transmitter antenna array 3108a.

[0393] As described above, the transmitter antenna array 3108a may include a transmitter antenna 3116, which may include... Figure 35A The first transmitter antenna 3116a, the second transmitter antenna 3116b, the third transmitter antenna 3116c, and the fourth transmitter antenna 3116d are shown. The transmitter antenna 3116 of the transmitter antenna array 3108a is... Figure 35A The diagram shows an n×m grid pattern, where both n and m are equal to 2. Although Figure 35A The transmitter antennas 3116 of the transmitter antenna array 3108a shown are arranged in a 2×2 grid pattern. However, it should be understood that the transmitter antennas 3116 of the transmitter antenna array 3108a can be arranged in any n×m grid pattern, where n and m are both multiples of 2. In some embodiments, the distance between each transmitter antenna 3116 and its nearest neighbor is...d It can be equal to 1.5λ. However, in other embodiments, the distance between each of the transmitter antennas 3116 and its nearest neighbor is... d It can be a number greater than or less than 1.5λ.

[0394] Now for reference Figure 35B , which shows Figure 34 The diagram illustrates another exemplary embodiment of the transmitter antenna array 3108a. However, it should be understood that the receiver antenna array 3128a can be similar to the transmitter antenna array 3108a, which includes a receiver antenna 3136 in the same direction as the transmitter antenna 3116. In some embodiments, the receiver antenna 3136 of the receiver antenna array 3128a may be wound in the opposite direction to its corresponding counterpart (i.e., the transmitter antenna 3116) of the transmitter antenna array 3108a.

[0395] As described above, the transmitter antenna array 3108a may include a transmitter antenna 3116, which may include... Figure 35B The first transmitter antenna 3116a, the second transmitter antenna 3116b, the third transmitter antenna 3116c, and the fourth transmitter antenna 3116d are shown. The transmitter antenna 3116 of the transmitter antenna array 3108a is... Figure 35B The diagram shows an arrangement of a 1×m grid pattern. Although Figure 35B The transmitter antennas 3116 of the transmitter antenna array 3108a shown are arranged in a 1×4 grid pattern, but it should be understood that the transmitter antennas 3116 of the transmitter antenna array 3108a can be arranged in any 1×m grid pattern, where m is a multiple of 4.

[0396] As described above, in some embodiments, the distance between each transmitter antenna 3116 and its nearest neighbor is... d It can be equal to 1.5 times the wavelength λ. However, in other embodiments, the distance between each of the transmitter antennas 3116 and its nearest neighbor is... d It can be a number greater than or less than 1.5 times the wavelength λ. For example, in some embodiments, it is the distance between each transmitter antenna 3116 and its nearest neighbor. d It can be less than the wavelength λ. However, in other embodiments, the distance between each of the transmitter antennas 3116 and its nearest neighbor is... d It can be a multiple of the wavelength λ.

[0397] Now for reference Figure 36The diagram illustrates an exemplary embodiment of a method 3600 for using network 3100 according to this disclosure. Figure 36 As shown, method 3600 typically includes the following steps: simultaneously transmitting a first wireless signal 3120a and a second wireless signal 3120b from a transmitter antenna array 3108 into a hollow waveguide 3104, the first wireless signal 3120a and the second wireless signal 3120b having input data (i.e., first input data and second input data, respectively) encoded in a modulation format (i.e., a first modulation format and a second modulation format, respectively) and having carrier frequencies (i.e., a first carrier frequency and a second carrier frequency, respectively) in the range between 300 GHz and 10 THz, the first wireless signal 3120a having LHCP and the second wireless signal 3120b having RHCP, such that the first wireless signal 3120a and the second wireless signal 3120b interact to form a linearly polarized wireless signal 3124 (step 3604).

[0398] In some embodiments, method 3600 further includes, prior to the transmission step (step 3604): generating a first radio signal 3120a by applying a first channel signal 3112a to a first transmitter antenna 3116a of transmitter antenna array 3108; generating a second radio signal 3120b by applying a second channel signal 3112b to a second transmitter antenna 3116b of transmitter antenna array 3108; and guiding a phase shift relative to the second channel signal 3112b in the first channel signal 3112a to guide a polarization angle in the linearly polarized radio signal 3124.

[0399] In some such implementations, method 3600 further includes receiving a polarization signal 3208, wherein guidance is further defined as guiding a phase shift of a first channel signal 3112a relative to a second channel signal 3112b based at least in part on the polarization signal 3208.

[0400] In some embodiments, the transmitter antenna array 3108 is a transmitter antenna array 3108a, the input data is a first input data, the modulation format is a first modulation format, the carrier frequency is a first carrier frequency, and the linearly polarized radio signal 3124 is a first linearly polarized radio signal 3124a. In such an implementation, method 3600 may further include: simultaneously transmitting a third wireless signal 3120c and a fourth wireless signal 3120d from a transmitter antenna array 3108a into a hollow waveguide 3104, the third wireless signal 3120c having third input data encoded in a third modulation format and having a third carrier frequency in the range of 300 GHz and 10 THz, and the fourth wireless signal 3120d having fourth input data encoded in a fourth modulation format and having a fourth carrier frequency in the range of 300 GHz and 10 THz, the third wireless signal 3120c having LHCP and the fourth wireless signal 3120d having RHCP, such that the third wireless signal 3120c and the fourth wireless signal 3120d interact to form a second linearly polarized wireless signal 3124b.

[0401] In some such embodiments, method 3600 further includes, prior to transmitting the third radio signal 3120c: generating the third radio signal 3120c by applying the third channel signal 3112c to the third transmitter antenna 3116c of the transmitter antenna array 3108a; generating the fourth radio signal 3120d by applying the fourth channel signal 3112d to the fourth transmitter antenna 3116d of the transmitter antenna array 3108a; and guiding a phase shift in the third channel signal 3112c relative to the fourth channel signal 3112d to guide a polarization angle in the second linearly polarized radio signal 3124b.

[0402] In some such implementations, method 3600 further includes receiving a polarization signal 3208, the guidance of which is further defined as guiding a phase shift of a third channel signal 3112c relative to a fourth channel signal 3112d based at least in part on the polarization signal 3208.

[0403] In some embodiments, the first linearly polarized wireless signal 3124a has a first polarization angle, and the second linearly polarized wireless signal 3124b has a second polarization angle, and the first polarization angle and the second polarization angle are offset within the range of 86.8° and 93.2°.

[0404] In some embodiments, the transmission steps are further defined as: transmitting a first wireless signal 3120a via a first transmitter antenna 3116a; transmitting a second wireless signal 3120b via a second transmitter antenna 3116b; transmitting a third wireless signal 3120c via a third transmitter antenna 3116c; and transmitting a fourth wireless signal 3120d via a fourth transmitter antenna 3116d; wherein the first transmitter antenna 3116a, the second transmitter antenna 3116b, the third transmitter antenna 3116c, and the fourth transmitter antenna 3116d are arranged in an n×m grid pattern, where n and m are at least 2, such as... Figure 35A As shown.

[0405] In other embodiments, the transmission steps are further defined as: transmitting a first wireless signal 3120a via a first transmitter antenna 3116a; transmitting a second wireless signal 3120b via a second transmitter antenna 3116b; transmitting a third wireless signal 3120c via a third transmitter antenna 3116c; and transmitting a fourth wireless signal 3120d via a fourth transmitter antenna 3116d; wherein the first transmitter antenna 3116a, the second transmitter antenna 3116b, the third transmitter antenna 3116c, and the fourth transmitter antenna 3116d are arranged in a 1×m grid pattern, where m is at least four, such as... Figure 35B As shown.

[0406] Now for reference Figure 37A The illustration shows a schematic diagram of an exemplary embodiment of a dual-polarization (dual-pol) transmitter network element 3700a (hereinafter referred to as "transmitter network element 3700a") constructed according to the present disclosure. Figure 37A As shown, transmitter network element 3700a may include: a dual-pol hollow waveguide, referred to hereinafter as a dual-pol hollow waveguide 3704 by way of example, which is configured to simultaneously propagate signals having a first polarization and a second polarization different from the first polarization; one or more modulators 3708a-n (e.g., Figure 37A The first modulator 3708a and the second modulator 3708b shown (collectively, “modulator 3708”) are configured to generate a first channel signal 3712a and a second channel signal 3712b (collectively, “channel signal 3712”); and one or more antennas 3716a-n (e.g., Figure 37A The first antenna 3716a and the second antenna 3716b shown (collectively referred to as "antenna 3716") are configured to receive a first channel signal 3712a and a second channel signal 3712b, and to couple the first channel signal 3712a to a double-pol hollow waveguide 3704 having a first polarization, and to couple the second channel signal 3712b to a double-pol hollow waveguide 3704 having a second polarization. Antenna 3716 may be similar to antenna 900 described above.

[0407] Channel signal 3712 is also referred to herein as “transmit channel signal 3712” (i.e., “first transmit channel signal 3712a” and “second transmit channel signal 3712b”) (when viewed from the perspective of transmitter network element 3700a) and “receive channel signal 3712” (i.e., “first receive channel signal 3712a” and “second receive channel signal 3712b”) (as shown in the image). Figure 37B (As shown). However, it should be understood that the received channel signal 3712 may have the same data and the same RF frequency as the transmitted channel signal 3712, although the received channel signal 3712 may exhibit linear distortion caused by the dual-pol hollow waveguide 3704 and / or antenna 3716.

[0408] In an embodiment where antenna 3716 includes a first antenna 3716a and a second antenna 3716b, the first antenna 3716a can be configured to apply a first polarization to the first transmit channel signal 3712a when the first antenna 3716a couples the first transmit channel signal 3712a into the dual-pol hollow waveguide 3704, and the second antenna 3716b can be configured to apply a second polarization to the second transmit channel signal 3712b when the second antenna 3716b couples the second transmit channel signal 3712b into the dual-pol hollow waveguide 3704.

[0409] The first transmit channel signal 3712a may have first data encoded in a first modulation format, and the second transmit channel signal 3712b may have second data encoded in a second modulation format. In some embodiments, the first modulator 3708a may be configured to generate the first transmit channel signal 3712a, and the second modulator 3708b may be configured to generate the second transmit channel signal 3712b, such that the first transmit channel signal 3712a has a first channel frequency and the second transmit channel signal 3712b has a second channel frequency, wherein the first channel frequency and the second channel frequency are in the range between 300 GHz and 10 THz. In such embodiments, the modulator 3708 may be described as performing "direct modulation". However, in other embodiments, each of the first modulator 3708a and the second modulator 3708b may include an intermediate frequency (IF) modulator configured to generate a first transmit channel signal 3712a and a second transmit channel signal 3712b, respectively, such that the first transmit channel signal 3712a has a first IF frequency lower than a first channel frequency, and the second transmit channel signal 3712b has a second IF frequency lower than a second channel frequency. In such embodiments, each of the first modulator 3708a and the second modulator 3708b may further include one or more upconverters (not shown) configured to receive the first transmit channel signal 3712a and the second transmit channel signal 3712b, respectively, and upconvert the first transmit channel signal 3712a and the second transmit channel signal 3712b, such that the first transmit channel signal 3712a has a first channel frequency and the second transmit channel signal 3712b has a second channel frequency, wherein the first channel frequency and the second channel frequency are in the range between 300 GHz and 10 THz. In such implementations, modulator 3708 can be described as performing "IF modulation".

[0410] The first and second modulation formats can be selected from the group consisting of: intensity modulation (IM) / direct detection (DD) (IM / DD); non-return-to-zero modulation (NRZ); pulse amplitude modulation-n (PAMn); IM-PAMn; m-quadrature amplitude modulation (mQAM); single-sideband modulation (SSB); quadrature phase shift keying (QPSK); and differential detection QPSK (DQPSK). In some embodiments, the first modulation format is the same as the second modulation format. However, in other embodiments, the first modulation format is different from the second modulation format. In embodiments where one or more of the first and second modulation formats are PAMn or IM-PAMn, n can be a power of 2 (e.g., 2, 4, 8, 16, 32, 64, etc.). Similarly, in embodiments where one or more of the first and second modulation formats are mQAM, m can be a power of 2 greater than or equal to 4 (e.g., 4, 8, 16, 32, 64, etc.). It should be understood that 4QAM (i.e., mQAM in embodiments where m equals 4) can be the same as QPSK.

[0411] In some implementations, the modulator 3708 may also be configured to receive one or more input signals 3720 (e.g., Figure 37A The first input signal 3720a, the second input signal 3720b, the third input signal 3720c, and the fourth input signal 3720d shown are collectively referred to as "input signals 3720". In some such embodiments, such as Figure 37A As shown, the first input signal 3720a and the second input signal 3720b can form a first pair of input signals 3724a, and the third input signal 3720c and the fourth input signal 3720d can form a second pair of input signals 3724b. In this embodiment, the first pair of input signals 3724a can have first data encoded in a first modulation format, and the second pair of input signals 3724b can have second data encoded in a second modulation format. Furthermore, in this embodiment, the first input signal 3720a and the third input signal 3720c can be I input signals, and the second input signal 3720b and the fourth input signal 3720d can be Q input signals.

[0412] The first polarization can be orthogonal to the second polarization. In some embodiments, the first polarization is left-handed circular polarization (LHCP). In such embodiments, the second polarization is right-handed circular polarization (RHCP). In other embodiments, the first polarization is horizontal linear polarization (HLP). In such embodiments, the second polarization is vertical linear polarization (VLP). Those skilled in the art will understand that the HLP and VLP can be rotated such that the HLP is not perfectly horizontal and the VLP is not perfectly vertical.

[0413] Now for reference Figure 37B The diagram illustrates another exemplary embodiment of a dual-pol receiver network element 3700b (hereinafter referred to as "receiver network element 3700b") constructed according to the present disclosure. Figure 37B As shown, receiver network element 3700b may include a dual-pol hollow waveguide 3704 and an antenna 3716 configured to receive a first receive channel signal 3712a and a second receive channel signal 3712b from the dual-pol hollow waveguide 3704 (e.g., Figure 37B The first antenna 3716a and the second antenna 116b shown), and one or more demodulators 3728a-n configured to receive the first receive channel signal 3712a and the second receive channel signal 3712b (e.g., Figure 37B The first demodulator 3728a and the second demodulator 3728b shown (collectively referred to as "demodulator 3728")

[0414] In some implementations, the demodulator 3728 may also be configured to generate one or more output signals 3732 based on the first received channel signal 3712a and the second received channel signal 3712b (e.g., Figure 37B The first output signal 3732a, the second output signal 3732b, the third output signal 3732c, and the fourth output signal 3732d shown in the figure (collectively referred to as "output signal 3732") (that is, the first output signal 3732a and the second output signal 3732b are generated based on the first received channel signal 3712a, and the third output signal 3732c and the fourth output signal 3732d are generated based on the second received channel signal 3712b).

[0415] In some implementations, such as Figure 37B As shown, the first output signal 3732a and the second output signal 3732b can form a first pair of output signals 3736a. Similarly, the third output signal 3732c and the fourth output signal 3732d can form a second pair of output signals 3736b. In this specific embodiment, the first output signal 3732a and / or the third output signal 3732c may have in-phase (I) data, and the second output signal 3732b and / or the fourth output signal 3732d may have quadrature (Q) data. The output signal 3732 can be configured for data detection (i.e., extraction of the first and second data).

[0416] In an embodiment where antenna 3716 includes a first antenna 3716a and a second antenna 3716b, the first antenna 3716a may be configured to receive an RF signal with a first polarization, and the second antenna 3716b may be configured to receive an RF signal with a second polarization.

[0417] In some embodiments, the first demodulator 3728a and the second demodulator 3728b can be configured to demodulate the first received channel signal 3712a and the second received channel signal 3712b, respectively, to generate a first pair of output signals 3736a (i.e., first output signal 3732a and second output signal 3732b) based on the first received channel signal 3712a, and to generate a second pair of output signals 3736b (i.e., third output signal 3732c and fourth output signal 3732d) based on the second received channel signal 3712b, such that the first output signal 3732a and the second output signal 3732b in the first pair of output signals 3736a have a first channel frequency in the range between 300 GHz and 10 THz, and the third output signal 3732c and the fourth output signal 3732d in the second pair of output signals 3736b have a second channel frequency. In such an embodiment, the demodulator 3728 can be described as performing "direct demodulation". However, in other embodiments, each of the first demodulator 3728a and the second demodulator 3728b may include one or more downconverters (not shown) configured to receive the first receive channel signal 3712a and the second receive channel signal 3712b, respectively, and downconvert the first receive channel signal 3712a and the second receive channel signal 3712b such that the first receive channel signal 3712a has a first intermediate frequency less than the first channel frequency, and the second receive channel signal 3712b has a second intermediate frequency less than the second channel frequency. In such a specific embodiment, each of the first demodulator 3728a and the second demodulator 3728b may further include an IF demodulator configured to demodulate the first received channel signal 3712a and the second received channel signal 3712b, respectively, to generate a first pair of output signals 3736a (i.e., a first output signal 3732a and a second output signal 3732b) based on the first received channel signal 3712a and a second pair of output signals 3736b (i.e., a third output signal 3732c and a fourth output signal 3732d) based on the second received channel signal 3712b. In such an embodiment, demodulator 3728 can be described as performing "IF demodulation".

[0418] Now for reference Figure 38 The diagram illustrates a dual-pol signal 3800 comprising multiple wavelength division multiplexing (WDM) signals 3804 according to the present disclosure. The dual-pol signal 3800 is also referred to herein as "transmit dual-pol signal 3800" when viewed from the perspective of transmitter network element 3700a, and when viewed from the perspective of receiver network element 3700b (…). Figure 37BWhen viewed from the perspective of (as shown in the diagram), the dual POL signal 3800 is also referred to herein as "received dual POL signal 3800". However, it should be understood that the received dual POL signal 3800 may have the same data and the same frequency as the transmitted dual POL signal 3800, but the received dual POL signal 3800 may exhibit linear distortion caused by the hollow waveguide 3704 and / or antenna 3716 of the dual POL. Similarly, when viewed from the perspective of transmitter network element 3700a, the WDM signal 3804 is also referred to herein as "transmitted WDM signal 3804", and when viewed from the perspective of receiver network element 3700b, the WDM signal 3804 is also referred to herein as "received WDM signal 3804" (as shown in the diagram). Figure 37B (As shown). However, it should be understood that the received WDM signal 804 can have the same data and the same frequency as the transmitted WDM signal 3804, although the received WDM signal 804 may exhibit linear distortion caused by the dual-pol hollow waveguide 3704 and / or antenna 3716.

[0419] As will be discussed in more detail below, in some embodiments, transmitter network element 3700a can be configured to transmit multiple transmit WDM signals 3804 (e.g., Figure 38 The first transmitted WDM signal 3804a and the second transmitted WDM signal 3804b shown are transmitted dual POL signals 3800, wherein each of the transmitted WDM signals 3804 includes a plurality of transmitted channel signals 3712, wherein each of the transmitted channel signals 3712 has a channel frequency in the range of 300 GHz and 10 THz. Transmitter network element 3700a can be configured to transmit at least one of the plurality of transmitted WDM signals 3804 (i.e., a single channel with a single polarization). Similarly, in some embodiments, receiver network element 3700b can be configured to receive a received dual POL signal 3800 having a plurality of received WDM signals 3804, wherein each of the received WDM signals 3804 includes a plurality of received channel signals 3712, wherein each of the received channel signals 3712 has a channel frequency in the range of 300 GHz and 10 THz.

[0420] The first WDM signal 3804a is in Figure 38 The middle is shown as having multiple first channel signals 3712a (e.g., Figure 38 The first f1 channel signal 3712a-1, the first f2 channel signal 3712a-2, the first f3 channel signal 3712a-3, and the first f4 channel signal 3712a-4 shown in the diagram (collectively referred to as "first channel signal 3712a"). Similarly, the second WDM signal 3804b in Figure 38The middle is shown as having multiple second channel signals 3712b (e.g., Figure 38 The second f1 channel signal 3712b-1, the second f2 channel signal 3712b-2, the second f3 channel signal 3712b-3, and the second f4 channel signal 3712b-4 shown in the figure (collectively referred to as "second channel signal 3712b").

[0421] like Figure 38 As shown, the first f1 channel signal 3712a-1 and the second f1 channel signal 3712b-1 may have a first channel frequency f1, the first f2 channel signal 3712a-2 and the second f2 channel signal 3712b-2 may have a second channel frequency f2, the first f3 channel signal 3712a-3 and the second f3 channel signal 3712b-3 may have a third channel frequency f3, and the first f4 channel signal 3712a-4 and the second f4 channel signal 3712b-4 may have a fourth channel frequency f4. Each of the WDM signals 3804 may have at least one of the multiple channel signals 3712 (i.e., a single channel with a single polarization).

[0422] like Figure 38 As shown, in some such embodiments, adjacent first channel signals in the first channel signal 3712a may be spaced apart by 200 GHz, and adjacent second channel signals in the second channel signal 3712b may be spaced apart by 200 GHz. However, in other embodiments, adjacent first channel signals 3712a may be spaced apart by 50 GHz and 400 GHz, and adjacent second channel signals 3712b may be spaced apart by 50 GHz and 400 GHz.

[0423] Now for reference Figure 39 The illustration shows a schematic diagram of an exemplary embodiment of a dual-pol transmission network 3900 constructed according to the present disclosure. Figure 39 As shown, the dual-pol transmission network 3900 may include a first dual-pol network element 3902a, a second dual-pol network element 3902b, and a dual-pol hollow waveguide 3704 extending between the first dual-pol network element 3902a and the second dual-pol network element 3902b. The dual-pol hollow waveguide 3704 is configured to simultaneously propagate signals having a first polarization and a second polarization different from the first polarization.

[0424] Although the transmission network 3900 is described herein as including a first dual-pol network element 3902a for transmitting a signal and a second dual-pol network element 3902b for receiving the signal, it should be understood that the transmission network 3900 may be bidirectional; that is, the transmission network 3900 may further include a second dual-pol network element 3902b for transmitting a signal and a first dual-pol network element 3902a for receiving the signal. Therefore, in some such embodiments, the dual-pol hollow waveguide 3704 may be bidirectional (i.e., configured to propagate signals simultaneously in both directions); however, in other such embodiments, the dual-pol hollow waveguide 3704 includes a first dual-pol hollow waveguide (not shown) configured to propagate a signal in a first direction (e.g., from the first dual-pol network element 3902a to the second dual-pol network element 3902b), and a second dual-pol hollow waveguide (not shown) configured to propagate a signal in a second direction opposite to the first direction (e.g., from the second dual-pol network element 3902b to the first dual-pol network element 3902a). However, the first dual POL network element 3902a is also referred to herein as "transmitter network element 3902a", and the second dual POL network element 3902b is also referred to herein as "receiver network element 3902b".

[0425] The transmitter dual-pol network element 3902a may include multiple modulators 3708 (e.g., Figure 39 The first f1 modulator 3708a-1, the second f1 modulator 3708b-1, the first f2 modulator 3708a-2, the second f2 modulator 3708b-2, the first f3 modulator 3708a-3, the second f3 modulator 3708b-3, the first f4 modulator 3708a-4 and the second f4 modulator 3708b-4 shown, the first combiner 3904a, the second combiner 3904b, the third combiner 3904c and one or more first dual POL antennas 3716c (hereinafter referred to as "first dual POL antenna 3716c").

[0426] The first f1 modulator 3708a-1, the first f2 modulator 3708a-2, the first f3 modulator 3708a-3, and the first f4 modulator 3708a-4 can be collectively referred to as "the first modulator 3708a", and the second f1 modulator 3708b-1, the second f2 modulator 3708b-2, the second f3 modulator 3708b-3, and the second f4 modulator 3708b-4 can be collectively referred to as "the second modulator 3708b". Although in Figure 39 Four modulators 3708 are shown, but it should be understood that the first modulator 3708a and the second modulator 3708b may include more than four modulators 3708.

[0427] Each of the first modulators 3708a can be configured to generate a specific one of the first transmit channel signals 3712a having first data encoded in a first modulation format. In some embodiments, each of the first modulators 3708a can be configured to generate a specific one of the first transmit channel signals 3712a such that each of the first transmit channel signals 3712a has one of a plurality of different first channel frequencies in the range between 300 GHz and 10 THz. In such embodiments, the first modulators 3708a can be described as performing “direct modulation”. However, in other embodiments, each of the first modulators 3708a may include an IF modulator configured to generate a specific one of the first transmit channel signals 3712a such that each of the first transmit channel signals 3712a has one of a plurality of different first intermediate frequencies less than the different first channel frequencies of this first transmit channel signal 3712a. In such embodiments, each of the first modulators 3708a may further include one or more first upconverters (not shown) configured to receive and upconvert the first transmit channel signal 3712a such that each of the first transmit channel signals 3712a has a first channel frequency different from that of the first transmit channel signal 3712a. In such embodiments, the first modulator 3708a may be described as performing "IF modulation".

[0428] In some embodiments, each of the first modulators 3708a may also be configured to receive a first pair of input signals 3724a, wherein each of the first pair of input signals 3724a has a first input signal 3720a, a second input signal 3720b, and first data encoded in a first modulation format.

[0429] Each of the second modulators 3708b can be configured to generate a specific one of the second transmit channel signals 3712b having second data encoded in a second modulation format. In some embodiments, each of the second modulators 3708b can be configured to generate a specific one of the second transmit channel signals 3712b such that each of the second transmit channel signals 3712b has one of a plurality of different second channel frequencies in the range between 300 GHz and 10 THz. In such embodiments, the second modulators 3708b can be described as performing “direct modulation”. However, in other embodiments, each of the second modulators 3708b may include an IF demodulator configured to generate a specific one of the second transmit channel signals 3712b such that each of the second transmit channel signals 3712b has one of a plurality of different second intermediate frequencies less than the different second channel frequencies of this second transmit channel signal 3712b. In such embodiments, each of the second modulators 3708b may further include one or more second upconverters (not shown) configured to receive and upconvert the second transmit channel signal 3712b, such that each of the second transmit channel signals 3712b has a channel frequency different from that of the second transmit channel signal 3712b. In such embodiments, the second modulator 3708b may be described as performing "IF modulation".

[0430] A first combiner 3904a may be configured to receive a first transmit channel signal 3712a from a first modulator 3708a and combine the first transmit channel signal 3712a into a first transmit WDM signal 3804a. A second combiner 3904b may be configured to receive a second transmit channel signal 3712b from a second modulator 3708b and combine the second transmit channel signal 3712b into a second transmit WDM signal 3804b. A third combiner 3904c may be configured to receive the first transmit WDM signal 3804a and the second transmit WDM signal 3804b, and combine the first transmit WDM signal 3804a and the second transmit WDM signal 3804b into a transmit dual POL signal 3800. One or more of the first combiner 3904a, the second combiner 3904b, and the third combiner 3904c may be multiplexers. In some implementations, one or more of the first combiner 3904a and the second combiner 3904b are WDM combiners, and the third combiner 3904c is a polarization combiner.

[0431] The first dual-pol antenna 3716c can be configured to receive the transmitted dual-pol signal 3800 from the third combiner 3904c and couple the transmitted dual-pol signal 3800 to the dual-pol hollow waveguide 3704 (i.e., a first transmitted WDM signal 3804a with a first polarization and a second transmitted WDM signal 3804b with a second polarization).

[0432] The receiver dual-pol network element 3902b may include multiple demodulators 3728 (e.g., Figure 39 The first f1 demodulator 3728a-1, the second f1 demodulator 3728b-1, the first f2 demodulator 3728a-2, the second f2 demodulator 3728b-2, the first f3 demodulator 3728a-3, the second f3 demodulator 3728b-3, the first f4 demodulator 3728a-4 and the second f4 demodulator 3728b-4 shown, the first splitter 3912a, the second splitter 3912b, the third splitter 3912c and one or more second dual POL antennas 3716d (hereinafter referred to as "second dual POL antennas 3716d").

[0433] The second dual-pol antenna 3716d can be configured to receive dual-pol signals 3800 (i.e., a first received WDM signal 3804a with a first polarization and a second received WDM signal 3804b with a second polarization) from the dual-pol hollow waveguide 3704.

[0434] The third splitter 3912c can be configured to receive a dual-Pol signal 3800 from the second dual-Pol antenna 3716d and split the received dual-Pol signal 3800 into a first received WDM signal 3804a and a second received WDM signal 3804b. The first splitter 3912a can be configured to receive the first received WDM signal 3804a from the third splitter 3912c and split the first received WDM signal 3804a into multiple first received channel signals 3712a. The second splitter 3912b can be configured to receive the second received WDM signal 3804b from the third splitter 3912c and split the second received WDM signal 3804b into multiple second received channel signals 3712b. One or more of the first splitter 3912a, the second splitter 3912b, and the third splitter 3912c can be demultiplexers. In some implementations, one or more of the first splitter 3912a and the second splitter 3912b are WDM splitters, and the third splitter 3912c is a polarization splitter.

[0435] The first f1 demodulator 3728a-1, the first f2 demodulator 3728a-2, the first f3 demodulator 3728a-3, and the first f4 demodulator 3728a-4 are collectively referred to as "first demodulator 3728a", and the second f1 demodulator 3728b-1, the second f2 demodulator 3728b-2, the second f3 demodulator 3728b-3, and the second f4 demodulator 3728b-4 are collectively referred to as "second demodulator 3728b". Although in Figure 39 Four demodulators 3728 are shown, but it should be understood that the first demodulator 3728a and the second demodulator 3728b may include more than four demodulators 3728.

[0436] Each of the first demodulators 3728a can be configured to demodulate a specific one of the first received channel signals 3712a to generate a first pair of output signals 3736a having first data encoded in a first modulation format and configured for data detection. In some embodiments, each of the first demodulators 3728a can be configured to demodulate a specific one of the first received channel signals 3712a having one of a plurality of different first channel frequencies in the range between 300 GHz and 10 THz. However, in other embodiments, the receiver dual-pol network element 3902b may also include one or more first downconverters (not shown) configured to receive the first received channel signals 3712a and downconvert the first received channel signals 3712a such that each of the first received channel signals 3712a has a first intermediate frequency (IF) among a plurality of different first channel frequencies less than the different first channel frequencies of the first received signal 3712a. In such an implementation, each of the first demodulators 3728a can be configured to demodulate a particular one of the first received channel signals 3712a having one of a plurality of different first intermediate frequencies.

[0437] Each of the second demodulators 3728b can be configured to demodulate a specific one of the second received channel signals 3712b to generate a second pair of output signals 3736b having second data encoded in a second modulation format and configured for data detection. In some embodiments, each of the second demodulators 3728b can be configured to demodulate a specific one of the second received channel signals 3712b having one of a plurality of different second channel frequencies in the range between 300 GHz and 10 THz. However, in other embodiments, the second dual-pol network element 3902b may also include one or more second downconverters (not shown) configured to receive the second received channel signals 3712b and downconvert the second received channel signals 3712b such that each of the second received channel signals 3712b has a second intermediate frequency (IF) of one of a plurality of different second IF frequencies less than the different second channel frequencies of the second received signal 3712b. In such an implementation, each of the second demodulators 3728b can be configured to demodulate a specific one of the second received channel signals 3712b having one of a plurality of different second intermediate frequencies.

[0438] Now for reference Figure 40 In some embodiments, the transmitter dual-pol network element 3902a may include a first antenna 3716e configured to transmit an RF signal with a first polarization and a second antenna 3716f configured to transmit an RF signal with a second polarization. In such an embodiment, the receiver dual-pol network element 3902b may include a third antenna 3716g configured to receive an RF signal with a first polarization and a fourth antenna 3716h configured to receive an RF signal with a second polarization. Each of the first antenna 3716e, the second antenna 3716f, the third antenna 3716g, and the fourth antenna 3716h may be a single-polarization or dual-polarization antenna.

[0439] Now for reference Figure 41 In some embodiments, the transmitter dual-pol network element 3902a may include a plurality of first antennas 3716e (e.g., first f1 antenna 3716e-1, first f2 antenna 3716e-2, first f3 antenna 3716e-3 and first f4 antenna 3716e-4) (collectively referred to as "first antennas 3716e") and a plurality of second antennas 3716f (e.g., second f1 antenna 3716f-1, second f2 antenna 3716f-2, second f3 antenna 3716f-3 and second f4 antenna 3716f-4) (collectively referred to as "second antennas 3716f").

[0440] Each of the first antennas 3716e can be configured to receive a specific one of the first transmit channel signals 3712a, and when the specific one of the first transmit channel signals 3712a is coupled into the dual-pol hollow waveguide 3704, a first polarization is applied to the specific one of the first transmit channel signals 3712a; and each of the second antennas 3716f can be configured to receive a specific one of the second transmit channel signals 3712b, and when the specific one of the second transmit channel signals 3712b is coupled into the dual-pol hollow waveguide 3704, a second polarization is applied to the specific one of the second transmit channel signals 3712b.

[0441] Similarly, in such an implementation, the receiver dual-pol network element 3902b may include a plurality of third antennas 3716g (e.g., third f1 antenna 3716g-1, third f2 antenna 3716g-2, third f3 antenna 3716g-3 and third f4 antenna 3716g-4) (collectively referred to as "third antennas 3716g") and a plurality of fourth antennas 3716h (e.g., fourth f1 antenna 3716h-1, fourth f2 antenna 3716h-2, fourth f3 antenna 3716h-3 and fourth f4 antenna 3716h-4) (collectively referred to as "fourth antennas 3716h").

[0442] Each of the third antennas 3716g can be configured to receive a specific one of the first receive channel signals 3712a with a first polarization from the dual-pol hollow waveguide 3704, and each of the fourth antennas 3716h can be configured to receive a specific one of the second receive channel signals 3712b with a second polarization from the dual-pol hollow waveguide 3704.

[0443] Now for reference Figure 42 , which shows Figure 37A A schematic diagram of an exemplary embodiment of the first modulator 3708a is shown. However, it should be understood that any modulator 3708 described herein may be similar to... Figure 42 The first modulator 3708a is shown. (As shown in the image...) Figure 42As shown, the first modulator 3708a may include a transmitter local oscillator (LO) 4200 configured to generate a transmitter LO signal 4204, a transmitter phase shifter 4208 configured to receive the transmitter LO signal 4204 and shift the phase of the transmitter LO signal 4204 by a predetermined amount (e.g., 90°) to generate a quadrature LO signal 4212, and a first transmitter mixer configured to receive the transmitter LO signal 4204 and a first input signal 3720a and mix the transmitter LO signal 4204 with the first input signal 3720a to generate a first transmitter mixer output signal 4220a. The transmitter mixer 4216a is configured to receive a quadrature LO signal 4212 and a second input signal 3720b and mix the quadrature LO signal 4212 with the second input signal 3720b to generate a second transmitter mixer output signal 4220b; and the transmitter adder 4224 is configured to receive a first transmitter mixer output signal 4220a and a second transmitter mixer output signal 4220b and combine the first transmitter mixer output signal 4220a and the second transmitter mixer output signal 4220b to generate a first transmit channel signal 3712a.

[0444] As described above, in some embodiments, the first modulator 3708a may be configured to generate a first transmit channel signal 3712a, such that the first transmit channel signal 3712a has a first channel frequency in the range of 300 GHz and 10 THz. However, in other embodiments, the first modulator 3708a may be configured to generate the first transmit channel signal 3712a, such that the first transmit channel signal 3712a has an intermediate frequency lower than the first channel frequency. In such embodiments, the first modulator 3708a may further include one or more upconverters (not shown) configured to receive the first transmit channel signal 3712a and upconvert the first transmit channel signal 3712a, such that the first transmit channel signal 3712a has the first channel frequency.

[0445] Now for reference Figure 43 , which shows Figure 37B The diagram illustrates an exemplary embodiment of the first demodulator 3728a. However, it should be understood that any demodulator 3728 described herein may be similar to... Figure 43 The first demodulator 3728a is shown. (As shown...) Figure 43As shown, the first demodulator 3728a may include a receiver LO 4300, which may be a voltage-controlled oscillator (VCO) configured to generate a receiver LO signal 4304 having an LO frequency within a predetermined range (e.g., 1 GHz) of a first channel frequency embedded in the first receive channel signal 3712a; a receiver phase shifter 4308 configured to receive the receiver LO signal 4304 and shift the phase of the receiver LO signal 4304 by a predetermined amount (e.g., 90°) to generate a quadrature LO signal 4312; and a first receiver mixer 4316a configured to receive the receiver LO signal 4304 and the first receive channel signal 3712a, and mix the receiver LO signal 4304 with the first receive channel signal 3712a to generate a first receive channel signal 4312. The receiver mixer output signal 4320a, the second receiver mixer 4316b, configured to receive the quadrature LO signal 4312 and the first receive channel signal 3712a, and mix the quadrature LO signal 4312 with the first receive channel signal 3712a to generate the second receiver mixer output signal 4320b, and the first low-pass filter (LPF) 4324a, configured to receive the first receiver mixer output signal 4320a and attenuate a frequency higher than a predetermined cutoff frequency to generate the first baseband signal 4322a (also referred to herein as "the first baseband signal"). "or "in-phase (I) channel"), the second LPF 4324b, which is configured to receive the output signal 4320b of the second receiver mixer and attenuate a frequency above a predetermined cutoff frequency to generate a second baseband signal 4322b (also referred to herein as " "or "or "quadrature (Q) channel"), carrier recovery module 4332, which is configured to receive a first baseband signal 4322a and a second baseband signal 4322b, and generate a carrier recovery control signal 4336 to match the LO frequency and LO phase of the receiver LO signal 4304 with the first channel frequency and first channel phase of the RF carrier embedded in the first received channel signal 3712a, module 4340, which has a configuration to form a complex signal representation The circuit system of the pre-equalized output signal 4344, and the equalizer 4348, are configured to apply a complex signal representation. Multiple complex tap weights are used to equalize the pre-equalized output signal 4344 to produce a first output signal 3732a configured for data detection, which is also in complex form (i.e., has I and Q components). The complex representation is mathematically convenient. The multiple complex tap weights can be determined and / or adjusted based on tap weight control algorithms such as Least Mean Square (LMS), Zero Forcing (ZF), etc. The operation of equalizer 4348 can be described as a convolution between the input signal (i.e., the pre-equalized output signal 4344) and the equalizer transfer function (which has a delayed-line finite impulse response (FIR) structure and multiple complex tap weights in the time domain), or a multiplication between the input signal (i.e., the pre-equalized output signal 4344) and the equalizer transfer function (which has a delayed-line FIR structure and multiple complex tap weights in the frequency domain). Those skilled in the art will understand that the equalizer transfer function can be determined based on the multiple complex tap weights.

[0446] It should be understood that the above description generally refers to receiver network element 3700a (in... Figure 37B (shown in), 3902b (in Figure 39 One or more of the embodiments shown in the figure include a coherent receiver. In other embodiments, such as those in which one or more of the first modulation format and the second modulation format are DQPSK, the first demodulator 3728a may lack one or more of the carrier recovery module 4332 and the receiver LO 4300; however, in such embodiments, the first demodulator 3728a may further include differential detection circuitry.

[0447] As described above, in some embodiments, the first demodulator 3728a may be configured to demodulate the first received channel signal 3712a to generate a first output signal 3732a, such that the first output signal 3732a has a first channel frequency in the range of 300 GHz and 10 THz. However, in other embodiments, the first demodulator 3728a may further include one or more downconverters (not shown) configured to downconvert the first received channel signal 3712a before demodulating it to generate the first output signal 3732a, such that the first received channel signal 3712a has an intermediate frequency (IF) lower than the first channel frequency. In such an embodiment, the first demodulator 3728a may further include one or more downconverters (not shown) configured to receive the first received channel signal 3712a and downconvert it, such that the first received channel signal 3712a has an IF lower than the first channel frequency.

[0448] Now for reference Figure 44The diagram illustrates another exemplary embodiment of the receiver network element 3700b constructed in accordance with the present disclosure. Figure 44 The receiver network element 3700b in the illustrated embodiment typically includes a first portion 4400a and a second portion 4400b. In some embodiments, the first portion 4400a is an X-pol portion, and the second portion 4400b is a Y-pol portion. In such embodiments, the first receive channel signal 3712a may be a receive X-pol signal, while the second receive channel signal 3712b may be a receive Y-pol signal. Figure 44 As shown, the receiver network unit 3700b may include a first demodulator 3728a, a second demodulator 3728b, and an equalizer 4402. Figure 44 As shown, equalizer 4402 may include multiple complex equalizers 4404 (e.g., Figure 44 The first complex equalizer 4404a, the second complex equalizer 4404b, the third complex equalizer 4404c, and the fourth complex equalizer 4404d shown) and multiple adders 4406 (e.g., Figure 44 The first adder 4406a and the second adder 4406b are shown.

[0449] It should be understood that although the first received channel signal 3712a (i.e., the X-pol signal) and the second received channel signal 3712b (i.e., the Y-pol signal) can use the same RF carrier, it may be necessary to include multiple carrier recovery modules (i.e., ...) in the receiver network element 3700b. Figure 44 The first carrier recovery module 4332-1 and the second carrier recovery module 4332-2 are shown.

[0450] Figure 44 The operation of modules 4340-1 and 4340-2 is similar to Figure 43 Module 4340 in the module. The first complex equalizer 4404a can be configured to receive the first pre-equalized output signal 4344-1 generated by the first demodulator 3728a and the first complex tap weight h. xx And the first pre-equalized output signal 4344-1 and the first complex tap weight h are combined. xx Multiply to generate the first equalizer intermediate signal 4408a.

[0451] The second complex equalizer 4404b can be configured to receive the second pre-equalized output signal 4344-2 and the second complex tap weight h generated by the second demodulator 3728b. yx And the second pre-equalized output signal 4344-2 and the second complex tap weight h yx Multiply to generate the second equalizer intermediate signal 4408b.

[0452] The third complex equalizer 4404c can be configured to receive the first pre-equalized output signal 4344-1 generated by the first demodulator 3728a and the third complex tap weight h. xy And the first pre-equalized output signal 4344-1 and the third complex tap weight h are combined. xy Multiply to generate the intermediate signal 4408c of the third equalizer.

[0453] The fourth complex equalizer 4404d can be configured to receive the second pre-equalized output signal 4344-2 generated by the second demodulator 3728b and the fourth complex tap weight h. yy And the second pre-equalized output signal 4344-2 and the fourth complex tap weight h are combined. yy Multiply to generate the fourth equalizer intermediate signal 4408d.

[0454] The first adder 4406a can be configured to receive a first equalizer intermediate signal 4408a generated by a first complex equalizer 4404a and a second equalizer intermediate signal 4408b generated by a second complex equalizer 4404b, and add the first equalizer intermediate signal 4408a and the second equalizer intermediate signal 4408b to generate a first output signal 3732a. In some embodiments, the first output signal 3732a is an equalized X-pol signal.

[0455] The second adder 4406b can be configured to receive a third equalizer intermediate signal 4408c generated by a third complex equalizer 4404c and a fourth equalizer intermediate signal 4408d generated by a fourth complex equalizer 4404d, and add the third equalizer intermediate signal 4408c and the fourth equalizer intermediate signal 4408d to generate a second output signal 3732b. In some embodiments, the second output signal 3732b is an equalized Y-pol signal.

[0456] It should be understood that when the system's cross-polarization decoupling is outside a predetermined range (e.g., between 16 dB and 25 dB, depending on the modulation format used and the system link budget), the second complex tap weight h yx and the third complex tap weight h xy It can be set to zero, which will result in Figure 44 The first part 4400a and the second part 4400b of the receiver network element 3700b operate as two separate single-polarization receiver network elements, such as Figure 43 As shown. In this configuration, receiver network element 3700b can operate more efficiently, thus requiring less power.

[0457] It should be understood that Figure 43 The implementation of the first demodulator 3728a shown in the figure and Figure 44 The implementation of receiver network element 3700b shown is an illustrative implementation provided as an example. It should also be understood that the above method can be referred to as an "analog method." Conversely, a "digital method" can also be used, which may include one or more ADCs and digital signal processors (DSPs) configured to perform the demodulation and equalization described herein.

[0458] In some embodiments, the first demodulator 3728a and the second demodulator 3728b may be configured to demodulate the first channel signal 3712a and the second channel signal 3712b, respectively, to generate a first input signal 3720a and a second input signal 3720b, such that the first input signal 3720a has a first channel frequency in the range of 300 GHz and 10 THz, and the second input signal 3720b has a second channel frequency. However, in other embodiments, the first demodulator 3728a may be configured to down-convert the first channel signal 3712a before demodulating it to generate the first input signal 3720a, such that the first channel signal 3712a has an intermediate frequency (IF) lower than the first channel frequency. In such embodiments, the first demodulator 3728a may further include one or more downconverters (not shown) configured to receive the first channel signal 3712a and down-convert it, such that the first channel signal 3712a has an IF lower than the first channel frequency. Similarly, in such an embodiment, the second demodulator 3728b may be configured to down-convert the second channel signal 3712b before demodulating it to generate the second input signal 3720b, such that the second channel signal 3712b has an intermediate frequency (IF) lower than the second channel frequency. In such an embodiment, the second demodulator 3728b may further include one or more downconverters (not shown) configured to receive the second channel signal 3712b and down-convert it, such that the second channel signal 3712b has an IF lower than the second channel frequency.

[0459] Now for reference Figure 45 The diagram illustrates an exemplary embodiment of the method of use 4500 according to this disclosure. Figure 45As shown, method 4500 typically includes the following steps: coupling a first wavelength division multiplexing (WDM) signal 3804a to a hollow waveguide (e.g., a double-pol hollow waveguide 3704 with a first polarization) via one or more antennas 900, 3716, and coupling a second WDM signal 3804b to a hollow waveguide (e.g., a double-pol hollow waveguide 3704 with a second polarization) so as to simultaneously propagate RF signals with the first and second polarizations through the double-pol hollow waveguide 3704, the first WDM signal 3804a having a first channel frequency in the range between 300 GHz and 10 THz, and the second WDM signal 3804b having a second channel frequency in the range between 300 GHz and 10 THz (step 4504).

[0460] In some embodiments, coupling the first WDM signal 3804a and the second WDM signal 3804b into the dual-pol hollow waveguide 3704 (step 4504) includes coupling the first WDM signal 3804a and the second WDM signal 3804b with modulation formats selected from the group consisting of: intensity modulation (IM) / direct detection (DD) (IM / DD); non-return-to-zero modulation (NRZ); pulse amplitude modulation-n (PAMn); IM-PAMn; m-quadrature amplitude modulation (mQAM); quadrature phase shift keying (QPSK); differential detection QPSK (DQPSK); and single-sideband modulation (SSB).

[0461] In some embodiments, coupling the first WDM signal 3804a and the second WDM signal 3804b into the dual-pol hollow waveguide 3704 (step 4504) includes coupling the first WDM signal 3804a to a first antenna 3716e configured to apply a first polarization, and coupling the second WDM signal 3804b to a second antenna 3716f configured to apply a second polarization, wherein the first antenna 3716e is separated from the second antenna 3716f.

[0462] In some embodiments, the first polarization is left-handed circular polarization (LHCP), and the second polarization is right-handed circular polarization (RHCP). In some embodiments, the first polarization is horizontal linear polarization (HLP), and the second polarization is vertical linear polarization (VLP).

[0463] In some embodiments, coupling the first WDM signal 3804a and the second WDM signal 3804b into the dual-pol hollow waveguide 3704 (step 4504) includes coupling the first WDM signal 3804a and the second WDM signal 3804b into a dual-pol antenna (e.g., a first dual-pol antenna 3716c), which is configured to simultaneously transmit RF signals having a first polarization and a second polarization into the dual-pol hollow waveguide 3704.

[0464] In some embodiments, method 4500 further includes the step of combining a plurality of first channel signals 3712a to form a first WDM signal 3804a, the first channel signals having a plurality of channel frequencies in the range of 300 GHz and 10 THz, and wherein at least some of the first channel signals are data-encoded. In some such embodiments, adjacent first channel signals 3712a are spaced apart in the range of 50 GHz to 400 GHz.

[0465] Now for reference Figure 46A The diagram illustrates another exemplary embodiment of a network element 4600 constructed according to this disclosure. Figure 46A As shown, network element 4600 typically includes one or more demodulators 4604 (hereinafter referred to as "demodulator 4604") and one or more modulators 4608 (hereinafter referred to as "modulator 4608"), which are as follows: Figure 46A It is shown to be coupled to one or more buses or circuits.

[0466] Demodulator 4604 can be configured to receive one or more input signals 4612 (hereinafter referred to as "input signals 4612"), for example Figure 46A The first input signal 4612a and the second input signal 4612b are shown, and a series of phase signals 4616 (hereinafter referred to as "phase signals 4616") and a series of amplitude signals 4620 (hereinafter referred to as "amplitude signals 4620") are extracted from the input signal 4612. The demodulator 4604 can be configured to decouple the input signal 4612 into separate bit streams and generate the phase signals 4616 and amplitude signals 4620 based on the separate bit streams. The demodulator 4604 can therefore be configured to extract the first phase signal 4616a and the first amplitude signal 4620a from the first input signal 4612a. Similarly, the demodulator 4604 can be configured to extract the second phase signal 4616b and the second amplitude signal 4620b from the second input signal 4612b.

[0467] Input signal 4612 may have input data encoded therein. For example, first input signal 4612a may have first input data encoded therein, and second input signal 4612b may have second input data encoded therein. As described in more detail below, the first input data and the second input data may be encoded in the first input signal 4612a and the second input signal 4612b respectively in a first modulation format, which may be pulse amplitude modulation (PAM). n )Format.

[0468] Modulator 4608 can be configured to receive phase signal 4616 and amplitude signal 4620, and modulate phase signal 4616 and amplitude signal 4620, which indicate first input data and second input data, onto output signal 4624, such that output signal 4624 has first input data and second input data encoded in a second modulation format. Output signal 4624 may have a carrier frequency in THz band 104. In some embodiments, the carrier frequency is in the range between 500 GHz and 10 THz. As described in more detail below, modulator 4608 can also be configured to receive or generate local oscillator (LO) signal 5012, which is an electrical signal in the range of 500 GHz to 10 THz (in Figure 50A and 50B As shown in the diagram, phase signal 4616 and amplitude signal 4620 are modulated onto local oscillator (LO) signal 5012 to generate output signal 4624. Furthermore, as described in more detail below, the second modulation format may differ from the first modulation format.

[0469] In some embodiments, the first modulation format is Pulse Amplitude Modulation-n (PAMn) format, and the second modulation format is m-quadrature amplitude modulation (mQAM) format. In some such embodiments, the first modulation format is Pulse Amplitude Modulation-4 (PAM4) format, and the second modulation format is 16-quadrature amplitude modulation (16QAM) format. However, in other embodiments, the first and second modulation formats can be modulation formats other than PAMn, PAM4, mQAM, or 16QAM.

[0470] Now for reference Figure 46B The diagram illustrates another exemplary embodiment of a network element 4600 constructed according to this disclosure. Figure 46BAs shown, in some embodiments, network element 4600 further includes antenna 4628 configured to receive output signal 4624 and couple output signal 4624 into hollow waveguide 4632. In some embodiments, hollow waveguide 4632 is an optical fiber (hollow or solid) configured to propagate electromagnetic waves in THz band 104. Antenna 4628 is coupled to modulator 4608 via one or more signal paths, which may be a bus or circuit.

[0471] Now for reference Figure 47A The diagram illustrates an exemplary embodiment of a demodulator 4604 constructed according to the present disclosure. Figure 47A As shown, demodulator 4604 may include a first splitter 4700a and a second splitter 4700b, one or more phase demodulators 4704 (hereinafter referred to as "phase demodulators 4704") and one or more amplitude demodulators 4708 (hereinafter referred to as "amplitude demodulators 4708"), as shown in the figure. Figure 47A It is shown to be coupled to one or more buses or circuits.

[0472] The first splitter 4700a and the second splitter 4700b can be configured to receive the first input signal 4612a and the second input signal 4612b, respectively, and to split the first input signal 4612a and the second input signal 4612b into at least two pre-demodulated signals 4712 (hereinafter referred to as "pre-demodulated signals 4712"). For example, the first splitter 4700a can be configured to receive the first input signal 4612a and split the first input signal 4612a into... Figure 47A The first pre-demodulated signal 4712a and the second pre-demodulated signal 4712b are shown, and the second splitter 4700b can be configured to receive the second input signal 4612b and split the second input signal 4612b into Figure 47A The third pre-demodulation signal 4712c and the fourth pre-demodulation signal 4712d are shown.

[0473] Phase demodulator 4704 may include a first phase demodulator 4704a and a second phase demodulator 4704b. The first phase demodulator 4704a may be configured to extract a series of first phase signals 4616a from a first pre-demodulated signal 4712a, and the second phase demodulator 4704b may be configured to extract a series of second phase signals 4616b from a third pre-demodulated signal 4712c, such that the first phase signals 4616a and the second phase signals 4616b are synchronized and can be used to represent input data encoded into the input signal 4612.

[0474] The amplitude demodulator 4708 may include a first amplitude demodulator 4708a and a second amplitude demodulator 4708b. The first amplitude demodulator 4708a may be configured to extract a first amplitude signal 4620a from a second pre-demodulated signal 4712b, and the second amplitude demodulator 4708b may be configured to extract a second amplitude signal 4620b from a fourth pre-demodulated signal 4712d.

[0475] Now for reference Figure 47B The diagram illustrates another exemplary embodiment of the demodulator 4604a constructed according to this disclosure. Figure 47B As shown, demodulator 4604a may include clock and data recovery circuitry (CDR) 4716, which is configured to extract a first phase signal 4616a and a first amplitude signal 4620a from a first input signal 4612a, and to extract a second phase signal 4616b and a second amplitude signal 4620b from a second input signal 4612b. That is, similar to demodulator 4604 described above, CDR circuitry 4716 may be configured to decouple the input signal 4612a into separate bitstreams and generate phase signal 4616a and amplitude signal 4620b based on the separate bitstreams. As described herein, the CDR circuit 4716 may be similar to a conventional CDR circuit because the CDR circuit 4716 of this disclosure receives an input signal 4612 (e.g., a PAM4 signal); however, unlike a conventional CDR circuit that can provide a signal with the same modulation format (e.g., a PAM4 signal) as an output, the CDR circuit 4716 of this disclosure can provide a phase signal 4616 and an amplitude signal 4620 as outputs.

[0476] Now for reference Figure 48 The illustration shows a schematic diagram of an exemplary embodiment of a first phase demodulator 4704a constructed according to the present disclosure. However, it should be understood that any of the phase demodulators 4704 described herein may be similar in form and function to... Figure 48 The first phase demodulator 4704a is shown. (Example) Figure 48 As shown, the first phase demodulator 4704a may include an amplifier 4800, a first AC coupler 4804a, and a first comparator 4808a, as follows: Figure 48 It is shown to be coupled to one or more buses or circuits.

[0477] Amplifier 4800 can be configured to receive a first pre-demodulated signal 4712a (in electrical form) and limit the amplitude of the first pre-demodulated signal 4712a to generate a limiting signal 4812 (in electrical form). In some embodiments, amplifier 4800 is a limiting amplifier.

[0478] The first AC coupler 4804a can be configured to receive the limiting signal 4812 and block the passage of a direct current (DC) signal while allowing the passage of an AC signal, thereby removing any DC offset from the limiting signal 4812 to generate a first threshold-centered signal 4816a, wherein the first threshold-centered signal 4816a is centered on a predetermined threshold voltage. In some embodiments, the predetermined threshold voltage is zero.

[0479] The first comparator 4808a can be configured to receive a first threshold-centered signal 4816a and determine the polarity (i.e., positive or negative) of the first threshold-centered signal 4816a to generate a first phase signal 4616a (in electrical form). In some embodiments, the first comparator 4808a is a sign-checking comparator.

[0480] Now for reference Figure 49 The diagram illustrates an exemplary embodiment of a first amplitude demodulator 4708a constructed according to the present disclosure. However, it should be understood that any of the amplitude demodulators 4708 described herein may be similar in form and function to... Figure 49 The first amplitude demodulator 4708a is shown. (As shown) Figure 49 As shown, the first amplitude demodulator 4708a may include an amplitude extraction circuit 4900, a second AC coupler 4804b, and a second comparator 4808b, as follows: Figure 49 It is shown to be coupled to one or more buses or circuits.

[0481] The amplitude extraction circuit 4900 can be configured to receive a second pre-demodulated signal 4712b (in electrical form) and determine the amplitude of the second pre-demodulated signal 4712b to generate a rectified signal 4904 (in electrical form). In some embodiments, the amplitude extraction circuit 4900 is a rectifier. In other embodiments, the amplitude extraction circuit 4900 can be, for example, a squaring circuit.

[0482] The second AC coupler 4804b can be configured to receive the rectified signal 4904 (in electrical form) and block the passage of the DC signal while allowing the passage of the AC signal, thereby removing any DC offset from the rectified signal 4904 to generate a second threshold-centered signal 4816b (in electrical form), wherein the second threshold-centered signal 4816b is centered at a predetermined threshold voltage. In some embodiments, the predetermined threshold voltage is zero.

[0483] The second comparator 4808b can be configured to receive a second threshold-centered signal 4816b and determine the polarity (i.e., positive or negative) of the second threshold-centered signal 4816b to generate a first amplitude signal 4620a (in electrical form). That is, if the polarity of the second threshold-centered signal 4816b is positive, the first amplitude signal 4620a can have a non-zero value (e.g., 1), and if the polarity of the second threshold-centered signal 4816b is negative, the first amplitude signal 4620a can have a zero value (i.e., 0). In some embodiments, the second comparator 4808b is a sign-checking comparator.

[0484] Now for reference Figure 50A The diagram illustrates an exemplary embodiment of a modulator 4608 constructed according to the present disclosure. Figure 50A As shown, modulator 4608 may include a third splitter 4700c, a first phase modulator 5000a, a second phase modulator 5000b, a first amplitude modulator 5004a, a second amplitude modulator 5004b, and a combiner 5008, which are coupled to one or more buses or circuits as shown in FIG. 50.

[0485] The third splitter 4700c can be configured to receive the LO signal 5012 generated by an LO generator (not shown) external to the modulator 4608, and split the LO signal 5012 into one or more unmodulated carrier signals 5016 (in electrical form) (hereinafter referred to as "unmodulated carrier signals 5016"). That is, the third splitter 4700c can be configured to receive the LO signal 5012 and split the LO signal 5012 into... Figure 50A The diagram shows a first unmodulated carrier signal 5016a (in electrical form) and a second unmodulated carrier signal 5016b (in electrical form). In some embodiments, the first unmodulated carrier signal 5016a may represent the I component of the output signal 4624, and the second unmodulated carrier signal 5016b may represent the Q component of the output signal 4624.

[0486] The first phase modulator 5000a can be configured to receive a first unmodulated carrier signal 5016a (i.e., the I component of the output signal 4624) and a first phase signal 4616a, and modulate the first phase signal 4616a onto the first unmodulated carrier signal 5016a to generate a first phase modulated carrier signal 5020a. The first amplitude modulator 5004a can be configured to receive the first phase modulated carrier signal 5020a and a first amplitude signal 4620a, and modulate the first amplitude signal 4620a onto the first phase modulated carrier signal 5020a to generate a first phase-amplitude modulated carrier signal 5024a.

[0487] The second phase modulator 5000b can be configured to receive a second unmodulated carrier signal 5016b (i.e., the Q component of the output signal 4624) and a second phase signal 4616b, and modulate the second phase signal 4616b onto the second unmodulated carrier signal 5016b to generate a second phase modulated carrier signal 5020b. The second amplitude modulator 5004b can be configured to receive the second phase modulated carrier signal 5020b and the second amplitude signal 4620b, and modulate the second amplitude signal 4620b onto the second phase modulated carrier signal 5020b to generate a second phase-amplitude modulated carrier signal 5024b.

[0488] The combiner 5008 can be configured to receive a first phase amplitude modulation carrier signal 5024a and a second phase amplitude modulation carrier signal 5024b, and combine the first phase amplitude modulation carrier signal 5024a and the second phase amplitude modulation carrier signal 5024b to generate an output signal 4624, such that the output signal 4624 is encoded in a second modulation format.

[0489] In some embodiments, the LO signal 5012 has an LO frequency equal to the carrier frequency (i.e., a frequency in the range between 500 GHz and 10 THz). However, in other embodiments, the LO signal 5012 has an LO frequency less than the carrier frequency. In such embodiments, the combiner 5008 is configured to receive a first phase amplitude modulated carrier signal 5024a and a second phase amplitude modulated carrier signal 5024b, and combine the first phase amplitude modulated carrier signal 5024a and the second phase amplitude modulated carrier signal 5024b to generate an intermediate signal (not shown) having an LO frequency, and the network element 4600 further includes an upconverter (not shown) configured to receive the intermediate signal and upconvert the intermediate signal to generate an output signal 4624 (in electrical form) having a carrier frequency. In other embodiments, the LO signal 5012 has an LO frequency greater than the carrier frequency. In such an implementation, combiner 5008 is configured to receive a first phase amplitude modulation carrier signal 5024a and a second phase amplitude modulation carrier signal 5024b, and combine the first phase amplitude modulation carrier signal 5024a and the second phase amplitude modulation carrier signal 5024b to generate an intermediate signal (not shown) having an LO frequency, and network element 4600 further includes a downconverter (not shown) configured to receive the intermediate signal and downconvert the intermediate signal to generate an output signal 4624 (in electrical form) having a carrier frequency.

[0490] Now for reference Figure 50B The diagram illustrates another exemplary embodiment of the modulator 4608a constructed according to the present disclosure. Figure 50BAs shown, in some embodiments, the third splitter 4700c may be electrically coupled to the LO generator 5028 and receive the LO signal 5012 (in electrical form) from the LO generator 5028 inside the modulator 4608a.

[0491] In some embodiments, one or more of the first phase modulator 5000a and the second phase modulator 5000b include a lateral switch 5200 configured to select one of a 0° signal and a 180° signal (e.g., Figure 52 (As shown). In some specific embodiments, one or more of the first amplitude modulator 5004a and the second amplitude modulator 5004b include a switched attenuator (e.g., Figure 53A The PI type attenuator 5300a shown Figure 53B The T-type attenuator 5300b shown and Figure 53C The bridged T-type attenuator 5300c shown is configured to generate a signal having one of a first amplitude level and a second amplitude level. In other embodiments, one or more of the first amplitude modulator 5004a and the second amplitude modulator 5004b include one of a switching amplifier and a variable gain amplifier.

[0492] In some embodiments, the first amplitude level is 1V and the second amplitude level is 3V. However, in other embodiments, the first amplitude level is a number of volts greater than or less than 1, and the second amplitude level is a number of volts greater than or less than 3. In such embodiments, the first amplitude level may be a fraction of the second amplitude level (e.g., 1 / 4, 1 / 3, or 1 / 2).

[0493] Now for reference Figure 51 The diagram illustrates an exemplary embodiment of a method 5100 for performing direct modulation from a first modulation format to a second modulation format in a THz band 104. Figure 51As shown, method 5100 may include the following steps: receiving a first input signal 4612a and a second input signal 4612b by demodulator 4604. The first input signal 4612a has first input data, and the second input signal 4612b has second input data, the first input data and the second input data being encoded in a first modulation format (step 5104); extracting a first phase signal 4616a and a first amplitude signal 4620a from the first input signal 4612a and a second phase signal 4616b and a second amplitude signal 4620b from the second input signal 4612b by demodulator 4604 (step 5108); modulating the first phase signal 4616a, the first amplitude signal 4620a, and the second phase signal 4616b, and modulating the second amplitude signal 4620b onto an output signal 4624 by modulator 4608, such that the output signal 4624 is encoded in a second modulation format, the output signal 4624 having a modulation frequency range of 500 GHz and 2 GHz. The carrier frequency is within the range of THz (step 5112); the output signal 4624 is converted from an electrical signal to an electromagnetic wave through the antenna 4628 (step 5114); and the electromagnetic wave is coupled into the hollow waveguide 4632 through the antenna 4628 (step 5116).

[0494] In some implementations, receiving the first input signal 4612a and the second input signal 4612b (step 5104) is further defined as receiving the first input signal 4612a and the second input signal 4612b by the demodulator 4604, the first input signal 4612a having first input data and the second input signal 4612b having second input data, the first input data and the second input data being encoded in a first modulation format, wherein the first modulation format is PAMn (e.g., PAM4) format.

[0495] In some embodiments, extracting the first phase signal 4616a and the first amplitude signal 4620a from the first input signal 4612a and extracting the second phase signal 4616b and the second amplitude signal 4620b from the second input signal 4612b (step 5108) is further defined as the demodulator 4604 extracting the first phase signal 4616a and the first amplitude signal 4620a from the first input signal 4612a and extracting the second phase signal 4616b and the second amplitude signal 4620b from the second input signal 4612b, wherein the demodulator 4604 includes a CDR circuit 4716.

[0496] In some embodiments, extracting the first phase signal 4616a and the first amplitude signal 4620a from the first input signal 4612a and extracting the second phase signal 4616b and the second amplitude signal 4620b from the second input signal 4612b (step 5108) further includes: splitting the first input signal 4612a into a first pre-demodulated signal 4712a and a second pre-demodulated signal 4712b by the first splitter 4700a; and splitting the second input signal 4612b into a third pre-demodulated signal by the second splitter 4700b. Signal 4712c and fourth pre-demodulated signal 4712d; the first phase signal 4616a is extracted from the first pre-demodulated signal 4712a by the first phase demodulator 4704a; the first amplitude signal 4620a is extracted from the second pre-demodulated signal 4712b by the first amplitude demodulator 4708a; the second phase signal 4616b is extracted from the third pre-demodulated signal 4712c by the second phase demodulator 4704b; the second amplitude signal 4620b is extracted from the fourth pre-demodulated signal 4712d by the second amplitude demodulator 4708b.

[0497] In some embodiments, extracting the first phase signal 4616a and the first amplitude signal 4620a from the first input signal 4612a and extracting the second phase signal 4616b and the second amplitude signal 4620b from the second input signal 4612b (step 5108) is further defined as follows: the first phase signal 4616a is obtained from the first pre-demodulated signal 4712a by the first phase demodulator 4704a through passing the first pre-demodulated signal 4712a to the amplifier 4800, the amplifier 4800 having an output connected to the input of the first comparator 4808a; the first amplitude demodulator 4708a extracts the first phase signal 4616a from the second pre-demodulated signal 4712b by passing the second pre-demodulated signal 4712b to the amplitude extraction circuit 4900. 12b extracts the first amplitude signal 4620a, and the amplitude extraction circuit 4900 has an output connected to the input of the second comparator 4808b; the second phase demodulator 4704b extracts the second phase signal 4616b from the third pre-demodulated signal 4712c by passing the third pre-demodulated signal 4712c to the amplifier 4800, and the amplifier 4800 has an output connected to the input of the first comparator 4808a; and the second amplitude demodulator 4708b extracts the second amplitude signal 4620b from the fourth pre-demodulated signal 4712d by passing the fourth pre-demodulated signal 4712d to the amplitude extraction circuit 4900, and the amplitude extraction circuit 4900 has an output connected to the input of the second comparator 4808b.

[0498] In some embodiments, modulating the first phase signal 4616a, the first amplitude signal 4620a, the second phase signal 4616b, and the second amplitude signal 4620b onto the output signal 4624 (step 5112) is further defined as modulating the first phase signal 4616a, the first amplitude signal 4620a, the second phase signal 4616b, and the second amplitude signal 4620b onto the output signal 4624 by the modulator 4608 such that the output signal 4624 is encoded in a second modulation format having a carrier frequency in the range between 500 GHz and 2 THz, wherein the second modulation format is mQAM (e.g., 16QAM) format.

[0499] In some embodiments, modulating the first phase signal 4616a, the first amplitude signal 4620a, the second phase signal 4616b, and the second amplitude signal 4620b onto the output signal 4624 (step 5112) further includes: splitting the LO signal 5012 into a first unmodulated carrier signal 5016a and a second unmodulated carrier signal 5016b by a third splitter 4700c; modulating the first phase signal 4616a onto the first unmodulated carrier signal 5016a by a first phase modulator 5000a; and modulating the first amplitude signal 4620a onto the first unmodulated carrier signal 5016a by a first amplitude modulator 5004a (i.e., the first phase modulated carrier signal 4616a). The second phase signal 4616b is modulated onto the second unmodulated carrier signal 5016b by the second phase modulator 5000b; the second amplitude signal 4620b is modulated onto the second unmodulated carrier signal 5016b (i.e., the second phase modulated carrier signal 5020b) by the second amplitude modulator 5004b; and the first unmodulated carrier signal 5016a (i.e., the first phase amplitude modulated carrier signal 5024a) and the second unmodulated carrier signal 5016b (i.e., the second phase amplitude modulated carrier signal 5024b) are combined by the combiner 5008 to form an output signal 4624, such that the output signal 4624 is encoded in the second modulation format.

[0500] In some embodiments, modulating the first phase signal 4616a, the first amplitude signal 4620a, the second phase signal 4616b, and the second amplitude signal 4620b onto the output signal 4624 (step 5112) further includes: splitting the LO signal 5012 into a first unmodulated carrier signal 5016a and a second unmodulated carrier signal 5016b by a third splitter 4700c; modulating the first amplitude signal 4620a onto the first unmodulated carrier signal 5016a by a first amplitude modulator 5004a; and modulating the first phase signal 4616a onto the first unmodulated carrier signal 5016a by a first phase modulator 5000a. The first phase signal 4616a is modulated onto the first unmodulated carrier signal 5016a; the second amplitude signal 4620b is modulated onto the second unmodulated carrier signal 5016b by the second amplitude modulator 5004b; the second phase signal 4616b is modulated onto the second unmodulated carrier signal 5016b by the second phase modulator 5000b; and the first unmodulated carrier signal 5016a and the second unmodulated carrier signal 5016b are combined by the combiner 5008 to form an output signal 4624, such that the output signal 4624 is encoded in the second modulation format.

[0501] In some embodiments, modulating the first phase signal 4616a, the first amplitude signal 4620a, the second phase signal 4616b, and the second amplitude signal 4620b onto the output signal 4624 (step 5112) is further defined as: modulating the first phase signal 4616a onto the first unmodulated carrier signal 5016a by the first phase modulator 5000a, wherein the first phase modulator 5000a is a first cross switch; modulating the first amplitude signal 4620a onto the first unmodulated carrier signal 5016a by the first amplitude modulator 5004a (i.e., the first phase signal 4616a, the first amplitude signal 4620a, the second amplitude signal 4620b ... The second phase signal 4616b is modulated onto the second unmodulated carrier signal 5016b by the second phase modulator 5000b, wherein the second phase modulator 5000b is a second cross switch; and the second amplitude signal 4620b is modulated onto the second unmodulated carrier signal 5016b (i.e., the second phase modulated carrier signal 5020b) by the second amplitude modulator 5004b, wherein the second amplitude modulator 5004b is a second cross switch.

[0502] Now for reference Figure 54 Another exemplary embodiment of the transceiver 5400a constructed in accordance with the present disclosure is shown therein.

[0503] Now for reference Figure 55 Another exemplary embodiment of the transceiver 5400b constructed in accordance with the present disclosure is shown.

[0504] Now for reference Figure 56Another exemplary embodiment of the transceiver 5400c constructed in accordance with the present disclosure is shown therein.

[0505] Now for reference Figure 57 Another exemplary embodiment of the transmitter 5700a constructed in accordance with the present disclosure is shown therein.

[0506] Now for reference Figure 58 Another exemplary embodiment of a receiver 5800 constructed in accordance with the present disclosure is shown therein.

[0507] Now for reference Figure 59 The present invention illustrates another exemplary embodiment of the transmitter 5700b constructed in accordance with the present disclosure.

[0508] Now for reference Figure 60 Another exemplary embodiment of the transmitter 5700c constructed in accordance with the present disclosure is shown.

[0509] Now for reference Figures 61-63 The illustration shows an exemplary embodiment of a differential circuit constructed according to the present disclosure, including a first differential circuit 6100a (e.g., Figure 61 (as shown), the second differential circuit 6100b (as shown) Figure 62 (as shown) and the third differential circuit 6100c (as shown) Figure 63 (As shown).

[0510] Now for reference Figure 64 An exemplary embodiment of an antenna array 6400 constructed in accordance with the present disclosure is shown therein.

[0511] Now for reference Figure 65 The illustration shows a perspective view of an exemplary embodiment of an antenna 6500 constructed and used in accordance with this disclosure. Figure 65 As shown, the antenna 6500 includes an electromagnetic absorber 6502 disposed around one or more radiators 6504 (e.g., a first radiator 6504a, a second radiator 6504b, a third radiator 6504c, and a fourth radiator 6504d). As described above, the one or more radiators 6504 can be constructed according to the radiator 908. It should be understood that, although in Figure 65 Four radiators 6504 are shown, but antenna 6500 may include more or fewer than four radiators 6504, such as one radiator 6504 or eight radiators 6504 (for example).

[0512] In one embodiment, one or more of the radiators 6504 may be mounted to corresponding ground planes 904a-d. For example, a first radiator 6504a may be mounted to a first ground plane 904a, a second radiator 6504b may be mounted to a second ground plane 904b, a third radiator 6504c may be mounted to a third ground plane 904c, and a fourth radiator 6504d may be mounted to a fourth ground plane 904d (not shown).

[0513] In some specific embodiments, one or more radiators in radiator 6504 may be disposed within hollow waveguide 208. Figure 65 (Not shown in the image). In other embodiments, one or more radiators of radiator 6504 may be separate from and coaxially arranged with the hollow waveguide 208. In some embodiments, one or more radiators 6504 may be coupled to an optically coupled RF transmitter (such as the first transmitter 212a), while other radiators 6504 may be coupled to an optically coupled RF receiver (such as the first receiver 216a).

[0514] In one embodiment, the electromagnetic absorber 6502 is not disposed between the radiator 6504 (e.g., the first radiator 6504a, the second radiator 6504b, the third radiator 6504c, and the fourth radiator 6504d) and the hollow waveguide 208. In some embodiments, the electromagnetic absorber 6502 may include a distal surface 6508, an opposing proximal surface 6509, and one or more openings 6510 formed in the distal surface 6508 and extending toward the opposing proximal surface 6509. Figure 11 In the specific embodiment shown, four openings 6510 are illustrated by way of example, wherein one of the radiators 6504 is located in each of the four openings 6510.

[0515] In some non-limiting embodiments, only one radiator in radiator 6504 is positioned within a specific opening in opening 6510. Electromagnetic absorber 6502 has a plurality of inner surfaces 6511 defining opening 6510. Each inner surface 6511 surrounds one radiator in radiator 6504 positioned within a corresponding opening 6510. In the illustrated example, electromagnetic absorber 6502 does not have a cover covering any opening 6510, allowing electromagnetic waves generated by radiators 6504a-d to enter the hollow waveguide 208 directly. In specific embodiments where a cover is incorporated over one or more openings 6510, the cover may be selected from a material that is transparent (or largely transparent) to electromagnetic waves. For example, the cover may comprise a plastic material. The cover may cause less than 10% of the reflected power of the electromagnetic waves. Opposing proximal surfaces 6509 may be positioned adjacent to ground planes 90a-d. In some embodiments, opposing proximal surfaces 6509 contact ground planes 90a-d.

[0516] In one embodiment, each opening 6510 may have a cross-sectional shape similar in shape to the radiator 6504. In some embodiments, the cross-sectional shape of the opening 6510 may be set to be separated from the radiator 6504 by an opening distance based on the wavelength of the electromagnetic wave and / or the pattern of the radiator 6504 or the antenna 900. For example, the opening distance (e.g., the distance between the radiator 6504 and the inner surface 6511) may be at least 1 / 4 of the wavelength of the electromagnetic wave.

[0517] In one embodiment, the electromagnetic absorber 6502 may be disposed adjacent to the hollow waveguide 208. For example, the distal surface 6508 of the electromagnetic absorber 6502 may have a diameter defining a cross-sectional dimension. a The distal surface 6508 may contact the hollow waveguide 208. In other embodiments, the electromagnetic absorber 6502 may be disposed abutting against the hollow waveguide 208, for example, in contact with or touching the hollow waveguide 208. In other embodiments, the electromagnetic absorber 6502 may have a peripheral surface 6512 disposed within the hollow waveguide 208 and adjacent to or in contact with the inner surface 312 of the hollow waveguide 208. The diameter defining the cross-sectional dimension... a The electromagnetic wave can have data encoded within a carrier frequency range of at least 4 to 50 wavelengths, having wavelengths in the range of 300 GHz to 10 THz. In some embodiments, the peripheral surface 6512 has a cylindrical shape. However, it should be understood that the peripheral surface 6512 can be provided with another shape, such as a series of planes and adjacently arranged portions, to provide a cross-section such as rectangular, hexagonal, or octagonal. In some embodiments, the peripheral surface 6512 can have a non-uniform or unusual shape.

[0518] In one embodiment, the electromagnetic absorber 6502 may be made of an EM absorbing material selected to absorb, suppress, and / or otherwise limit the reflection of electromagnetic waves (e.g., electromagnetic waves carrying a transmitted signal). In one embodiment, the EM absorbing material may be made of a porous and / or lossy material. In some embodiments, the EM absorbing material is made of a semi-porous material having a plurality of randomly positioned and sized openings, the size of which is approximately the wavelength of the electromagnetic wave, i.e., between 1 / 100 and about 2 times the wavelength of the electromagnetic wave, and preferably about 1 / 4 of the wavelength of the electromagnetic wave. In some embodiments, the EM absorbing material has a texture similar to steel wool. In some embodiments, for example, as... Figure 67 As shown and discussed in detail below, the EM absorbing material can be configured as part of the ground plane 904. In one embodiment, the EM absorbing material may include, for example, a poorly conductive material (i.e., a material with low electrical conductivity), such as a carbon material or a carbon-containing compound. In other embodiments, different poorly conductive materials other than carbon may be selected.

[0519] In one embodiment, the EM absorbing material may be composed of a foam (e.g., a solid continuous phase material). The foam may be, for example, an open-cell foam, a closed-cell foam, or a combination thereof. The foam may be carbon-doped or carbon-loaded, i.e., the foam may have carbon absorbed / adsorbed into and disposed within the foam. In some embodiments, the foam is a polyurethane foam. In one embodiment, the EM absorbing material is a colloidal suspension having carbon particles suspended in a continuous phase material.

[0520] Now for reference Figure 66 The figure shows a cross-sectional view of another exemplary embodiment of an electromagnetic absorber 6600 constructed according to the present disclosure. As shown, the electromagnetic absorber 6600 may be disposed around one or more radiators 6504 (such as a first radiator 6504a and a second radiator 6504b) and disposed within a hollow waveguide 208 (shown as a sixth hollow waveguide 208f). As described above, in some embodiments, the first radiator 6504a and the second radiator 6504b may be attached to one or more ground planes 904, such as... Figure 65 As shown. In one embodiment, the electromagnetic absorber 6600 can be constructed according to the electromagnetic absorber 6502 detailed above, for example, constructed from an EM absorbing material.

[0521] In one specific embodiment, the sixth hollow waveguide 208f may have an inner surface 312 that defines a cavity 6604 and has a diameter that defines a cross-sectional dimension. d The sixth hollow waveguide 208f can be constructed based on any of the hollow waveguides 208a-n described in more detail above; however, Figure 66 The sixth hollow waveguide 208f shown is illustrated as a hollow-core optical fiber cable having a conductive layer 316 surrounding the dielectric layer 308. In other embodiments, the sixth hollow waveguide 208f may be a metallic non-optical waveguide.

[0522] The electromagnetic absorber 6600 may have a peripheral surface 6608 that contacts at least a portion of the inner surface 312 of the sixth hollow waveguide 208f (i.e., the hollow fiber optic cable). In some embodiments, the electromagnetic absorber 6600 has a diameter defined as less than or equal to that of the sixth hollow waveguide 208f. d The diameter of the cross-section a This allows the electromagnetic absorber 6600 to be extended or fitted into the cavity 6604 of the sixth hollow waveguide 208f so as not to interfere with the radiator 6504 that receives energy from electromagnetic waves.

[0523] In one embodiment, the sixth hollow waveguide 208f further includes a tapered section 6612 having a first end 6614 and a second end 6616. The first end 6614 may have an inner diameter. t And the second end 6616 can have a diameter d This causes the diameter of the sixth hollow waveguide 208f within the conical section 6612 to decrease from the diameter of... d Change to inner diameter t As shown in the figure, the inner diameter t It can be smaller than the diameter d .

[0524] In one embodiment, the electromagnetic absorber 6600 may extend within the sixth hollow waveguide 208f. In some embodiments, the electromagnetic absorber 6600 extends beyond the tapered section 6612 of the sixth hollow waveguide 208f. In other embodiments, the electromagnetic absorber 6600 extends only within the tapered section 6612 of the sixth hollow waveguide 208f. In one specific embodiment, as... Figure 66 As shown, the electromagnetic absorber 6600 can extend within the first portion 6620 of the tapered section 6612 of the sixth hollow waveguide 208f.

[0525] In some embodiments, the electromagnetic absorber 6600 within the sixth hollow waveguide 208f may be provided with a thickness 6622. The thickness 6622 may be uniform within the tapered section 6612 (e.g., within the first portion 6620 of the tapered section 6612). In other embodiments, the electromagnetic absorber 6600 within the sixth hollow waveguide 208f may be provided with a varying thickness 6622, such that the thickness 6622 tapers from the distal surface 6624 of the electromagnetic absorber 6600 to the inner end 6626 of the electromagnetic absorber 6600, for example, tapering to a feather edge, as shown by the tapered absorber surface 6628 (which is shown in dashed lines). The tapered absorber surface 6628 may taper at different rates from the distal surface 6624 to the inner end 6626 of the electromagnetic absorber 6600.

[0526] Now for reference Figure 67 The figure shows a cross-sectional view of an exemplary embodiment of an electromagnetic absorber 6700 constructed according to the present disclosure. As shown, the electromagnetic absorber 6700 can be integrated into a fifth ground plane 904e. In this embodiment, the electromagnetic absorber 6700 may include a plurality of vias 6712 having a via diameter 6704 and a depth 6708. The plurality of vias 6712 may extend from a first surface 6714a of the fifth ground plane 904e toward a second surface 6714b to a depth 6708. In some embodiments, the depth 6708 may extend through at least one layer 6716 of the fifth ground plane 904e, such as a first layer 6716a. Although the vias 6712 are described as having a via diameter 6704, the vias 6712 may have a cross-section of any suitable shape, such as elliptical, square, circular, or any unusual shape. In such embodiments, the via diameter 6704 may be, for example, a cross-sectional dimension.

[0527] In some embodiments, one or more of the plurality of vias 6712 of the electromagnetic absorber 6700 may extend through the first layer 6716a, while other vias of the plurality of vias 6712 may extend through the first layer 6716a and the second layer 6716b. As those skilled in the art will understand, some of the vias 6712 may be characterized as blind vias, meaning that the via 6712 extends through the first layer 6716a but not through the second layer 6716b, or through vias, meaning that the via 6712 extends through both the first layer 6716a and the second layer 6716b.

[0528] In some embodiments, the depth 6708 of the plurality of vias 6712 can be selected based on the wavelength of the electromagnetic wave. For example, the depth 6708 can be approximately one wavelength. In other embodiments, the depth 6708 can be between 1 / 10 and 10 wavelengths. In some embodiments, the plurality of vias 6712 may extend through multiple layers 6716 to reach the depth 6708, and in some implementations may not extend through all layers 6716. In some embodiments, a first set of the plurality of vias 6712 may be configured such that the depth 6708 is a first depth, and a second set of the plurality of vias 6712 may be configured such that the depth 6708 is a second depth different from the first depth, thereby forming a plurality of semi-perforated ground planes, wherein the array of vias 6712 extends between one or more semi-perforated ground planes. In one embodiment, the first set and the second set of vias 6712 may be randomly disposed within a first surface 6714a of the fifth ground plane 904e. In other embodiments, the first set and the second set may be disposed on the fifth ground plane 904e in a pattern selected to minimize the reflection of electromagnetic waves. In some implementations, the depth 6708 of one or more of the plurality of vias 6712 may be randomly selected to have a value between about 10% and about 1000% of the wavelength.

[0529] In some embodiments, the plurality of vias 6712 are spaced apart by a distance 6720. The distance 6720 can be selected based on the wavelength of the electromagnetic wave. For example, the distance 6720 can be approximately one wavelength. In other embodiments, the distance 6720 can be between approximately 1 / 10 of the wavelength and one wavelength.

[0530] In one embodiment, each of the plurality of vias 6712 may be defined by a via surface 6724 (i.e., a via) extending from a first surface 6714a to a second surface 6714b. In one embodiment, the surface 6724 of the via 6712 may be made of a material including, for example, copper, gold, and / or carbon. In some embodiments, one or more vias 6712 may extend through the first surface 6714a and the second surface 6714b. In some embodiments, the surface 6724 of the via 6712 may be made of a conductive material such as copper or gold, which is coated with an electrical dissipation material such as carbon to help absorb electromagnetic waves. In some embodiments, the via surface 6724 may be textured to help absorb electromagnetic waves. In some embodiments, the material may be an EM-absorbing material (as described above).

[0531] In some embodiments, the plurality of vias 6712 can be constructed by removing material from the fifth ground plane 904e. For example, during manufacturing, material can be removed from the first surface 6714a to a depth 6708 and having a via diameter 6704. In other embodiments, the plurality of vias 6712 can be constructed by extending protrusions 6726 from the second surface 6714b, such that the protrusions 6726 have a surface 6724, a height equal to the depth 6708, and are spaced apart from each other by a distance equal to the via diameter 6704.

[0532] In some embodiments, each of the plurality of vias 6712 may have a via diameter 6704 and an opening width 6730. In some embodiments, the via diameter 6704 may be the width of the via closest to the second surface 6714b. The via diameter 6704 may be the same as or different from the opening width 6730. In some embodiments, a first set of the plurality of vias 6712 may be configured such that the via diameter 6704 and the opening width 6730 are the same, a second set of the plurality of vias 6712 may be configured such that the via diameter 6704 is smaller than the opening width 6730, and a third set of the plurality of vias 6712 may be configured such that the via diameter 6704 is larger than the opening width 6730. The first set, second set, and third set of vias 6712 may be randomly disposed within the first surface 6714a of the fifth ground plane 904e. In some embodiments, the via diameter 6704 and the opening width 6730 of one or more of the plurality of vias 6712 may be randomly selected to have values ​​between about 10% and about 110% of the wavelength.

[0533] Now for reference Figure 68 The figure shows a cross-sectional view of an exemplary embodiment of an electromagnetic absorber 6800 constructed according to the present disclosure. As shown, the electromagnetic absorber 6800 is a sprayed coating configured as a low-THz electromagnetic absorber. In one embodiment, the electromagnetic absorber 6800 may be made of the material according to the electromagnetic absorber 6502 described above, for example, an EM absorbing material.

[0534] In one embodiment, the sprayed coating may be a carbon-loaded polyurethane foam that, when sprayed onto a substrate such as a ground plane 904, adheres to the ground plane 904 and forms an uneven or non-uniform coating, such as a carbon coating. The non-uniform coating may include carbon particles 6804 of varying sizes, resulting in a non-uniform coating with voids or pits 6808, the cross-sectional dimensions of which approximate the wavelength of an electromagnetic wave (e.g., about 300 μm). The non-uniform coating may have a thickness 6812 of at least one-quarter of the wavelength. In some embodiments, the non-uniform coating may have a thickness 6812 between about one wavelength and about ten wavelengths of an electromagnetic wave.

[0535] Now for reference Figure 69 The figure illustrates an exemplary embodiment of an electromagnetic absorber 6900 constructed according to the present disclosure. As shown, the electromagnetic absorber 6900 may be a fabric 6904 coated with an EM absorbing material (such as carbon). The fabric 6904 may be coated, for example, by using a sprayed carbon coating with an adhesive to allow the carbon to adhere to the fabric 6904. In some embodiments, the fabric 6904 may include a carbon-doped fabric.

[0536] In one embodiment, fabric 6904 may be formed from multiple strands 6908 (e.g., weft yarns 6908a and warp yarns 6908b) coated (or doped) with carbon particles or another poorly conductive EM absorbing material. In some embodiments, the strands 6908 of fabric 6904 may be carbon-doped before the formation of fabric 6904, while in other embodiments, the strands 6908 may be doped after the fabric 6904 is constructed.

[0537] In some embodiments, the fabric 6904 may be formed of a carbon-doped solid continuous phase material and has one or more voids 6920 disposed therethrough and defined by the remaining fabric 6904. In some embodiments, carbon particles may be ejected through the voids 6920 of the continuous phase material.

[0538] Now for reference Figure 70 The diagram illustrates a flowchart of an exemplary embodiment of process 7000 constructed according to the present disclosure. Process 7000 typically includes the steps of: disposing an electromagnetic absorber around the radiator of an antenna (step 7004); and coupling a hollow waveguide to the antenna (step 7008).

[0539] In one embodiment, placing the electromagnetic absorber around the radiator of the antenna (step 7004) includes placing the electromagnetic absorber (e.g., any one of electromagnetic absorber 6502, electromagnetic absorber 6600, electromagnetic absorber 6700, electromagnetic absorber 6800, and electromagnetic absorber 6900) around the radiator. In one embodiment, the electromagnetic absorber does not contact the radiator.

[0540] In one implementation, arranging an electromagnetic absorber around the radiator of the antenna (step 7004) may include arranging more than one electromagnetic absorber around the radiator of the antenna.

[0541] In one embodiment, placing the electromagnetic absorber around the radiator of the antenna (step 7004) includes positioning the electromagnetic absorber within a cavity 6604 of the hollow waveguide 208. In some embodiments, positioning the electromagnetic absorber within the cavity 6604 includes positioning the electromagnetic absorber so as not to interfere with the radiator 6504 that receives the energy of the electromagnetic waves.

[0542] In one embodiment, coupling the hollow waveguide to the antenna (step 7008) includes positioning the radiator 6504 within a cavity 6604 of the hollow waveguide 208 (or the sixth hollow waveguide 208f). In some embodiments, positioning the radiator 6504 within the cavity 6604 of the hollow waveguide 208 further includes positioning a peripheral surface 6512 within the hollow waveguide 208 and adjacent to or in contact with the inner surface 312 of the hollow waveguide 208. In one embodiment, coupling the hollow waveguide to the antenna (step 7008) includes positioning the radiator 6504 at least partially within the cavity 6604 of the hollow waveguide 208 (or the sixth hollow waveguide 208f).

[0543] In one embodiment, coupling the hollow waveguide to the antenna (step 7008) includes positioning the radiator 6504 within the tapered section 6612 of the sixth hollow waveguide 208f. In some embodiments, positioning the radiator 6504 within the tapered section 6612 includes configuring the peripheral surface 6608 of the electromagnetic absorber 6600 to abut against at least a first portion 6620 of the tapered section 6612 of the sixth hollow waveguide 208f.

[0544] In one embodiment, coupling the hollow waveguide to the antenna (step 7008) includes positioning the hollow waveguide 208 in contact with an electromagnetic absorber, for example against the distal surface 6508 of the electromagnetic absorber 6502 (or another electromagnetic absorber in the electromagnetic absorber).

[0545] Now for reference Figure 71 The document illustrates a process flow diagram of an exemplary embodiment of method 7100 constructed according to the present disclosure. Method 7100 generally includes the steps of: coupling an antenna and electromagnetic waves via a hollow waveguide (step 7104); and positioning an electromagnetic absorber around the antenna (step 7108). In one embodiment, coupling the antenna and electromagnetic waves via a hollow waveguide (step 7104) includes coupling a first antenna and a second antenna to the electromagnetic waves.

[0546] In one embodiment, coupling the antenna and electromagnetic waves via a hollow waveguide (step 7104) includes coupling the antenna and electromagnetic waves via a hollow waveguide, the hollow waveguide being at least one of: solid optical fiber, hollow optical fiber, and metallic non-optical waveguide. The coupling antenna and solid waveguide may include configuring an electromagnetic absorber surrounding the radiator of the antenna against the solid optical fiber. The coupling antenna and hollow optical fiber may include positioning the radiator of the antenna within a cavity 6604 of the hollow optical fiber (e.g., the sixth hollow waveguide 208f).

[0547] In one embodiment, positioning the electromagnetic absorber around the antenna (step 7108) includes placing the electromagnetic absorber around the radiator of the antenna. In some embodiments, placing the electromagnetic absorber around the radiator of the antenna also includes positioning the electromagnetic absorber against or in contact with the inner surface 312 of the cavity 6604 defining the sixth hollow waveguide 208f.

[0548] In some embodiments, placing the electromagnetic absorber around the radiator of the antenna also includes positioning the electromagnetic absorber against or in contact with the inner surface 312 (at least the first portion 6620) of the tapered section 6612 of the sixth hollow waveguide 208f.

[0549] In one embodiment, positioning the electromagnetic absorber around the antenna (step 7108) includes positioning the electromagnetic absorber (made of EM-absorbing material) near the ground plane 904. The electromagnetic absorber may be, for example, an absorbing carbon material sprayed onto the ground plane 904 to form a non-uniform carbon layer disposed on the ground plane (as referenced above). Figure 68 (as described).

[0550] In one embodiment, positioning the electromagnetic absorber around the antenna (step 7108) includes providing a plurality of vias 6712 within a ground plane 904. The plurality of vias 6712 may be positioned at a distance 6720 between each other at least one wavelength of the carrier frequency of the electromagnetic wave. In some embodiments, the plurality of vias 6712 have a via diameter 6704 of at least one wavelength of the carrier frequency. The vias 6712 may have any suitable cross-sectional geometry, such as circular, square, elliptical, etc., or any unusual shape. In some embodiments, one or more of the plurality of vias 6712 may be configured as through-vias within the ground plane, for example, vias 6712 extending from a first surface 6714a through a second surface 6714b. When the ground plane 904 includes more than one layer 6716, one or more of the plurality of vias 6712 may extend through one or more layers 6716 of the ground plane 904.

[0551] Now for reference Figure 72The diagram illustrates a process flow diagram of an exemplary embodiment of a fabrication process 7200 constructed according to the present disclosure. Fabrication process 7200 typically includes the following steps: selecting an absorber substrate (step 7204); providing a conductive material within the absorber substrate to generate an absorber precursor (step 7208); curing the absorber precursor into an EM absorbing material (step 7212); and attaching the EM absorbing material to an antenna (step 7216).

[0552] In one embodiment, selecting the absorber substrate (step 7204) includes selecting one or more of the following: foam (e.g., a solid continuous phase material), fabric (e.g., a woven or non-woven fabric), and spraying. In some embodiments, the selected absorber substrate may be selected as a component part. For example, selecting a foam may include selecting at least two component parts of the foam (e.g., isocyanate and polyol) that, when combined, result in foam formation. Similarly, selecting a fabric may include selecting components of the fabric, such as weft and warp yarns for woven fabrics, or chemical compound precursors for non-woven fabrics, and selecting a spray may include selecting accelerators, adhesives, and solvents.

[0553] In one embodiment, providing a conductive material to an absorber substrate to generate an absorber precursor (step 7208) may include absorbing, adsorbing, mixing, dissolving, suspending, coating, attaching, bonding, doping, and / or otherwise including the conductive material within the absorber substrate to generate the absorber precursor. For example, providing a conductive material having an absorber substrate may include spraying or coating a foam with a conductive material, spraying or coating a fabric with a conductive material such that the conductive material is disposed within the gaps between the warp and weft of a woven fabric or within one or more gaps formed in a nonwoven fabric, and bonding the conductive material to the sprayed layer.

[0554] In one embodiment, providing a conductive material having an absorber substrate to generate an absorber precursor (step 7208) may include absorption, adsorption, mixing, dissolving, suspending, coating, attaching, bonding, and / or otherwise including the conductive material being one or more of the following: carbon, fullerene, carbon nanoparticles, carbon compounds, half-metals, metalloids, etc., or combinations thereof. In one embodiment, providing a conductive material to an absorber substrate to generate an absorber precursor (step 7208) may include placing such a conductive material with the absorber substrate in a random position and / or orientation.

[0555] In one embodiment, providing a conductive material having an absorber substrate to generate an absorber precursor (step 7208) may include absorbing, adsorbing, mixing, dissolving, suspending, coating, attaching, bonding, and / or otherwise including the conductive material within one or more component portions of the absorber substrate. For example, the conductive material may be bonded to one or more of a component portion of a foam, a component portion of a sprayed material, and / ...

Claims

1. A transmitter, comprising: Client-side input, which is configured to receive one or more baseband signals containing client data; A transmitter circuit system configured to receive one or more baseband signals from the client side input and to generate one or more antenna feed signals based on the one or more baseband signals; as well as One or more antennas are configured to receive one or more antenna feed signals from the transmitter circuitry, generate one or more radiated signals based on the one or more antenna feed signals, and couple the one or more radiated signals into a hollow waveguide, each of the one or more radiated signals being a radiated electromagnetic wave configured for coherent detection and having a frequency in the range of 300 GHz and 10 THz.

2. The transmitter according to claim 1, wherein, Each of the one or more antennas is one of a differential waveguide probe antenna, a differential conical antenna, a differential patch antenna, a helical antenna, and a spiral antenna.

3. The transmitter according to claim 1, wherein, The one or more baseband signals include multiple parallel baseband signals and a serial baseband signal. The transmitter also includes a serializer configured to receive the multiple parallel baseband signals and combine the multiple parallel baseband signals into the serial baseband signal using at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM). The client-side input is configured to receive the serial baseband signal. The transmitter circuitry is configured to receive the serial baseband signal from the client-side input and generate the one or more antenna feed signals based on the serial baseband signal.

4. The transmitter according to claim 1, wherein, The one or more baseband signals include multiple parallel baseband signals and a serial baseband signal. The transmitter further includes a deserializer configured to receive the serial baseband signal and split the serial baseband signal into the multiple parallel baseband signals using at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM). The client-side input is configured to receive the multiple parallel baseband signals. The transmitter circuitry is configured to receive the multiple parallel baseband signals from the client-side input and generate the one or more antenna feed signals based on the multiple parallel baseband signals.

5. The transmitter according to claim 1, wherein, The frequency of the one or more radiated signals is a transmission frequency, and the transmitter circuit system includes: One or more local oscillators are configured to generate one or more carrier signals, each of the one or more carrier signals having a baseband frequency less than the transmission frequency; One or more modulation circuits configured to receive one or more baseband signals input from the client side and one or more carrier signals from one or more local oscillators, and to modulate the one or more baseband signals onto the one or more carrier signals to generate one or more modulated signals; and One or more upconversion circuits are configured to receive the one or more modulation signals from the one or more modulation circuits and upconvert the one or more modulation signals to generate the one or more antenna feed signals, each of the one or more antenna feed signals having the transmission frequency.

6. A receiver, comprising: One or more antennas are configured to coherently detect one or more radiated signals received from a hollow waveguide and generate one or more antenna output signals based on the one or more radiated signals, each of the one or more radiated signals being configured for coherent detection, having a frequency in the range of 300 GHz and 10 THz, and having radiated electromagnetic waves containing client data. A receiver circuit system configured to receive one or more antenna output signals from the one or more antennas and generate one or more baseband signals based on the one or more antenna output signals; as well as The client-side output is configured to receive one or more baseband signals from the receiver circuitry and to transmit the one or more baseband signals.

7. The receiver according to claim 6, wherein, Each of the one or more antennas is one of a differential waveguide probe antenna, a differential conical antenna, a differential patch antenna, a helical antenna, and a spiral antenna.

8. The receiver according to claim 6, wherein, The one or more baseband signals include multiple parallel baseband signals and a serial baseband signal. The receiver circuitry is configured to generate the serial baseband signal based on the output signals of the one or more antennas. The client-side output is configured to receive the serial baseband signal from the receiver circuitry and transmit the serial baseband signal. The receiver also includes a deserializer configured to receive the serial baseband signal and split the serial baseband signal into the multiple parallel baseband signals using at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM).

9. The receiver according to claim 6, wherein, The one or more baseband signals include multiple parallel baseband signals and a serial baseband signal. The receiver circuitry is configured to generate the multiple parallel baseband signals based on the output signals of the one or more antennas. The client-side output is configured to receive the multiple parallel baseband signals from the receiver circuitry and transmit the multiple parallel baseband signals. The receiver also includes a serializer configured to receive the multiple parallel baseband signals and combine the multiple parallel baseband signals into the serial baseband signal using at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM).

10. The receiver according to claim 6, wherein, The frequency of the one or more radiated signals is the transmission frequency, and the receiver circuit system includes: One or more local oscillators are configured to generate one or more reference signals, each of the one or more reference signals having a baseband frequency less than the transmission frequency; One or more down-conversion circuits configured to receive one or more antenna output signals from one or more antennas and one or more reference signals from one or more local oscillators, and to down-convert the one or more antenna output signals using the one or more reference signals to generate one or more modulated signals, each of the one or more modulated signals having the baseband frequency; and One or more demodulation circuits are configured to receive the one or more modulated signals from the one or more downconversion circuits and demodulate the one or more modulated signals to generate the one or more baseband signals.

11. A transceiver, comprising: Transmitter, including: The client-side input is configured to receive one or more first baseband signals having first client data. A transmitter circuitry system configured to receive one or more first baseband signals from the client side input, and to generate one or more antenna feed signals based on the one or more first baseband signals; and One or more first antennas configured to receive antenna feed signals from the transmitter circuitry, generate one or more first radiated signals based on the antenna feed signals, and couple the one or more first radiated signals into a first hollow waveguide, each of the one or more first radiated signals being a radiated electromagnetic wave configured for coherent detection and having a first frequency in the range of 300 GHz and 10 THz; and Receiver, including: One or more second antennas are configured to coherently detect one or more second radiated signals received from one of the first hollow waveguide and the second hollow waveguide, and to generate one or more antenna output signals based on the one or more second radiated signals, each of the one or more second radiated signals being configured for coherent detection, having a second frequency in the range of 300 GHz and 10 THz, and having radiated electromagnetic waves containing second client data. A receiver circuit system configured to receive one or more antenna output signals from the one or more second antennas, and to generate one or more second baseband signals based on the one or more antenna output signals; and The client-side output is configured to receive and transmit the one or more second baseband signals from the receiver circuitry.

12. The transceiver according to claim 11, wherein, Each of the one or more first antennas and the one or more second antennas is one of a differential waveguide probe antenna, a differential conical antenna, a differential patch antenna, a helical antenna, and a spiral antenna.

13. The transceiver according to claim 11, wherein, The one or more first baseband signals include a plurality of first parallel baseband signals and a first serial baseband signal, and the one or more second baseband signals include a plurality of second parallel baseband signals and a second serial baseband signal. The transmitter further includes a serializer configured to receive the plurality of first parallel baseband signals and combine the plurality of first parallel baseband signals into a first serial baseband signal using at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM). The client-side input is configured to receive the first serial baseband signal, and the transmitter circuitry is configured to receive the first serial baseband signal from the client-side input. The receiver circuitry is configured to receive the first serial baseband signal and generate the one or more antenna feed signals based on the first serial baseband signal. The receiver circuitry is configured to generate the second serial baseband signal based on the one or more antenna output signals. The client-side output is configured to receive the second serial baseband signal from the receiver circuitry and transmit the second serial baseband signal. The receiver also includes a deserializer configured to receive the second serial baseband signal from the client-side output and split the second serial baseband signal into the plurality of second parallel baseband signals using at least one of PDM, TDM, and WDM.

14. The transceiver according to claim 11, wherein, The one or more first baseband signals include a plurality of first parallel baseband signals and a first serial baseband signal, and the one or more second baseband signals include a plurality of second parallel baseband signals and a second serial baseband signal. The transmitter further includes a deserializer configured to receive the first serial baseband signal and split the first serial baseband signal into the plurality of first parallel baseband signals using at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM). The client-side input is configured to receive the plurality of first parallel baseband signals, and the transmitter circuitry is configured to receive from the client-side input. The receiver circuitry is configured to generate the plurality of second parallel baseband signals based on the plurality of first parallel baseband signals and to generate the plurality of antenna feed signals based on the plurality of first parallel baseband signals. The client-side output is configured to receive the plurality of second parallel baseband signals from the receiver circuitry and to transmit the plurality of second parallel baseband signals. The receiver also includes a serializer configured to receive the plurality of second parallel baseband signals and to combine the plurality of second parallel baseband signals into a second serial baseband signal using at least one of PDM, TDM, and WDM.

15. The transceiver according to claim 11, wherein, The first frequency of the one or more first radiated signals is a transmission frequency, and the transmitter circuit system includes: One or more first local oscillators are configured to generate one or more carrier signals, each of the one or more carrier signals having a first baseband frequency less than the transmission frequency; One or more modulation circuits configured to receive one or more first baseband signals input from the client side and one or more carrier signals from one or more first local oscillators, and to modulate the one or more first baseband signals onto the one or more carrier signals to generate one or more first modulated signals; and One or more upconversion circuits are configured to receive the one or more first modulation signals from the one or more modulation circuits and upconvert the one or more first modulation signals to generate the one or more antenna feed signals, each of the one or more antenna feed signals having the transmission frequency; The receiver circuit system includes: One or more second local oscillators are configured to generate one or more reference signals, each of the one or more reference signals having a second baseband frequency less than the transmission frequency; One or more down-conversion circuits configured to receive one or more antenna output signals from one or more second antennas and one or more reference signals from one or more second local oscillators, and to down-convert the one or more antenna output signals using the one or more reference signals to generate one or more second modulated signals, each of the one or more second modulated signals having a second baseband frequency; and One or more demodulation circuits are configured to receive the one or more second modulation signals from the one or more downconversion circuits and demodulate the one or more second modulation signals to generate the one or more second baseband signals.

16. The transmitter according to claim 1, wherein, The one or more baseband signals are multiple baseband signals, the one or more antenna feed signals are multiple antenna feed signals including combined antenna feed signals, the one or more radiated signals include combined radiated signals, the frequency of the one or more radiated signals is a transmission frequency, and the transmitter circuit system includes: Multiple local oscillators are configured to generate multiple carrier signals, each of the multiple carrier signals having a baseband frequency less than the transmission frequency; Multiple modulation circuits are configured to receive multiple baseband signals input from the client side and multiple carrier signals from the multiple local oscillators, and to modulate the multiple baseband signals onto the multiple carrier signals to generate multiple modulated signals; A plurality of upconversion circuits are configured to receive a plurality of modulated signals from the plurality of modulation circuits and upconvert the plurality of modulated signals to generate a plurality of upconverted signals; and A combiner configured to receive the plurality of up-converted signals from the plurality of up-converter circuits and combine the plurality of up-converted signals into the combined antenna feed signal; The one or more antennas are configured to receive the combined antenna feed signal from the combiner, generate the combined radiated signal based on the combined antenna feed signal, and couple the combined radiated signal into the hollow waveguide.

17. The transmitter according to claim 16, wherein, The multiple up-converted signals are combined into the combined antenna feed signal using at least one of time division multiplexing (TDM) and wavelength division multiplexing (WDM).

18. The receiver according to claim 6, wherein, The one or more baseband signals are multiple baseband signals, the one or more antenna output signals are multiple antenna output signals including combined antenna output signals, the one or more radiated signals include combined radiated signals, the frequency of the one or more radiated signals is a transmission frequency, the one or more antennas are configured to detect the combined radiated signals received from the hollow waveguide, and generate the combined antenna output signals based on the combined radiated signals, the receiver circuitry system including: A splitter is configured to receive the combined antenna output signal from the one or more antennas and to split the combined antenna output signal into the plurality of antenna output signals. Multiple local oscillators are configured to generate multiple reference signals, each of which has a baseband frequency less than the transmission frequency; A plurality of downconversion circuits are configured to receive the plurality of antenna output signals from the splitter and the plurality of reference signals from the plurality of local oscillators, and to downconvert the plurality of antenna output signals using the plurality of reference signals to generate a plurality of modulated signals, each of the plurality of modulated signals having the baseband frequency; and Multiple demodulation circuits are configured to receive the multiple modulation signals from the multiple downconversion circuits and demodulate the multiple modulation signals to generate the multiple baseband signals.

19. The receiver according to claim 18, wherein, The combined antenna output signal is split into multiple antenna output signals using at least one of time division multiplexing (TDM) and wavelength division multiplexing (WDM).

20. The transceiver according to claim 11, wherein, The one or more first baseband signals are multiple first baseband signals, the one or more antenna feed signals are multiple antenna feed signals including combined antenna feed signals, the one or more first radiated signals include a first combined radiated signal, the first frequency of the one or more first radiated signals is a transmission frequency, and the transmitter circuit system includes: Multiple local oscillators are configured to generate multiple carrier signals, each of the multiple carrier signals having a baseband frequency less than the transmission frequency; Multiple modulation circuits are configured to receive multiple first baseband signals input from the client side and multiple carrier signals from the multiple local oscillators, and to modulate the multiple first baseband signals onto the multiple carrier signals to generate multiple modulated signals; A plurality of upconversion circuits are configured to receive a plurality of modulated signals from the plurality of modulation circuits and upconvert the plurality of modulated signals to generate a plurality of upconverted signals; and A combiner configured to receive the plurality of up-converted signals from the plurality of up-converter circuits and combine the plurality of up-converted signals into the combined antenna feed signal; The one or more first antennas are configured to receive the combined antenna feed signal from the combiner, generate the first combined radiated signal based on the combined antenna feed signal, and couple the first combined radiated signal into the first hollow waveguide.

21. The transceiver according to claim 20, wherein, The multiple up-converted signals are combined into the combined antenna feed signal using at least one of time division multiplexing (TDM) and wavelength division multiplexing (WDM).

22. The transceiver according to claim 20, wherein, The one or more second baseband signals are a plurality of second baseband signals, the one or more antenna output signals are a plurality of antenna output signals including combined antenna output signals, the one or more second radiated signals include a second combined radiated signal, the second frequency of the one or more second radiated signals is a transmission frequency, the one or more second antennas are configured to detect the second combined radiated signal received from one of the first hollow waveguide and the second hollow waveguide, and to generate the combined antenna output signal based on the second combined radiated signal, the receiver circuit system including: A splitter is configured to receive the combined antenna output signal from the one or more second antennas and to split the combined antenna output signal into the plurality of antenna output signals. Multiple local oscillators are configured to generate multiple reference signals, each of which has a baseband frequency less than the transmission frequency; A plurality of downconversion circuits are configured to receive the plurality of antenna output signals from the splitter and the plurality of reference signals from the plurality of local oscillators, and to downconvert the plurality of antenna output signals using the plurality of reference signals to generate a plurality of modulated signals, each of the plurality of modulated signals having the baseband frequency; and Multiple demodulation circuits are configured to receive the multiple modulation signals from the multiple downconversion circuits and demodulate the multiple modulation signals to generate the multiple second baseband signals.

23. The transceiver according to claim 22, wherein, The combined antenna output signal is split into multiple antenna output signals using at least one of time division multiplexing (TDM) and wavelength division multiplexing (WDM).

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