A wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna

Abstract

This invention discloses a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna, comprising a first dielectric substrate, a metal layer, and a second dielectric substrate stacked together. Two rotationally symmetrical L-shaped patches are disposed on the first dielectric substrate. A split ring is disposed around the periphery of the two L-shaped patches, and several slits are uniformly cut along the circumferential direction of the split ring. A section of the metal layer is cut out in the middle to form a coupling slit. A microstrip feed line is disposed within the second dielectric substrate. The two L-shaped patches are connected to the metal layer through a first metallized via. A second metallized via is disposed at each slit of the split ring, passing through the first dielectric substrate and contacting the metal layer. A third metallized via is disposed in the gap between the L-shaped opening of the two L-shaped patches and the split ring, passing through the first dielectric substrate and contacting the metal layer. The advantages of this invention are: a 3-dB axial ratio beamwidth and a half-power beamwidth, thereby achieving communication over a wide angle range.

Description

Technical Field

[0001] This invention relates to the field of antenna technology, and more specifically to a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna. Background Technology

[0002] Modern wireless communication technology is rapidly developing to meet people's information needs. With the advent of the 5G era, millimeter-wave frequency bands are being utilized more and more, making the design of millimeter-wave antennas extremely important. Furthermore, compared to linearly polarized antennas, which can only receive waves of the same linear polarization, circularly polarized (CP) antennas can receive any linearly polarized wave, as well as circularly polarized waves, avoiding polarization loss caused by polarization mismatch between the transmitting and receiving antennas. CP antennas excel in solving polarization mismatch, suppressing rain and fog interference, and eliminating the Faraday effect. Therefore, the research and design of circularly polarized antennas in the millimeter-wave frequency band is crucial.

[0003] However, most current work on millimeter-wave circularly polarized antennas focuses on wide 3-dB axial ratio bandwidth, rather than widening the 3-dB axial ratio beamwidth and the half-power beamwidth of the radiation pattern. CP antennas with wide 3-dB axial ratio beamwidth and half-power beamwidth offer many advantages. For example, they are the best candidates for CP beam-scanning array element antennas, enabling communication over a wide angle range. Therefore, improving the 3-dB axial ratio beamwidth and half-power beamwidth of CP antennas is a pressing issue that needs to be addressed.

[0004] Chinese Patent Publication No. CN114566794A discloses a 5G millimeter-wave dual-polarized magnetoelectric dipole filter antenna, comprising a top dielectric substrate, a bottom dielectric substrate, and an intermediate adhesive layer. A radiator structure, a cross-shaped metal patch, and a ring-shaped metal structure are printed on the upper surface of the top dielectric substrate. The radiator structure is connected to the lower surface of the top dielectric substrate, and the cross-shaped metal patch is connected to the feed microstrip line of the bottom dielectric substrate. The ring-shaped metal structure surrounds the radiator structure. A metal ground is printed on the lower surface of the top dielectric substrate, with a circular slot applied to the metal ground. A circular ring patch is printed on the upper surface of the bottom dielectric substrate, and two sets of one-to-two feed microstrip lines are printed on the lower surface, with a stub line printed at the end of each microstrip line. The electric dipole length and magnetic dipole height control the low-frequency radiation null point. The ring-shaped metal structure and differential circuit control the high-frequency radiation null point. This antenna effectively improves out-of-band suppression and increases the antenna bandwidth to some extent. However, this antenna cannot achieve circular polarization and is not a circularly polarized antenna. It does not address how to improve the 3-dB axial ratio beamwidth and half-power beamwidth, thus making it difficult to achieve wide-angle communication. Summary of the Invention

[0005] The technical problem to be solved by this invention is how to improve the 3-dB axial ratio beamwidth and half-power beamwidth of the CP antenna, so as to achieve communication in a wide-angle range.

[0006] The present invention solves the above-mentioned technical problems through the following technical means: a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna, comprising a first dielectric substrate, a metal layer, and a second dielectric substrate stacked in layers. Two rotationally symmetrical L-shaped patches are provided on the first dielectric substrate. A split ring is provided around the periphery of the two L-shaped patches. The split ring is uniformly cut with several slits along its circumference. A piece is cut out in the middle of the metal layer to form a coupling slit. A microstrip feed line is provided in the second dielectric substrate. The two L-shaped patches are connected to the metal layer through a first metallized via. A second metallized via is provided at each slit of the split ring, and the second metallized via passes through the first dielectric substrate and contacts the metal layer. A third metallized via is provided in the gap between the L-shaped opening of the two L-shaped patches and the split ring, and the third metallized via passes through the first dielectric substrate and contacts the metal layer.

[0007] Beneficial effects: This invention improves the 3-dB axial ratio beamwidth of the antenna by adding split rings around the two L-shaped patches. By adding a second metallized via between the split ring gaps, the antenna radiation can be stretched in all directions due to its guiding effect, significantly widening the half-power beamwidth of the antenna. By adding a third metallized via between the split rings and the L-shaped patches, the antenna radiation is further stretched in two diagonal directions, further improving the half-power beamwidth of the antenna, thereby realizing communication over a wide angle range.

[0008] Furthermore, the two L-shaped patches are located on the upper surface of the first dielectric substrate, the metal layer is located on the lower surface of the first dielectric substrate, and the microstrip feed line is located on the lower surface of the second dielectric substrate.

[0009] Furthermore, the first dielectric substrate is a Rogers 4003C dielectric substrate with a dielectric constant of 3.55 and a loss tangent tanδ = 0.0027, and the second dielectric substrate is a Rogers 5880 dielectric substrate with a dielectric constant of 2.2 and a loss tangent tanδ = 0.0009.

[0010] Furthermore, a rectangular structure is cut out from the middle of the metal layer to form a rectangular coupling gap.

[0011] Furthermore, the lower part of the first metallized via is in contact with the coupling gap.

[0012] Furthermore, a portion of the microstrip feed line is located below the coupling gap.

[0013] Furthermore, the two L-shaped patches are equivalent to electric dipoles, and the coupling gap is equivalent to a magnetic dipole.

[0014] Furthermore, a feed port is provided at one end of the microstrip feed line located at the edge of the second dielectric substrate, and electromagnetic energy is coupled into the antenna from the feed port.

[0015] Furthermore, the heights of the first, second, and third metallized vias are one-quarter of the wavelength of the antenna's circular polarization center frequency, and the distance from the center of the first dielectric substrate to the split ring is the radiation aperture, which is equal to half the wavelength corresponding to the antenna's circular polarization center frequency.

[0016] Furthermore, by controlling the number and position of the second and / or third metallized vias, the radiation direction and radiation range of the antenna can be adjusted.

[0017] The advantages of this invention are:

[0018] (1) The present invention adds a split ring around the two L-shaped patches, which improves the 3-dB axial ratio beamwidth of the antenna. By adding a second metallized via between the gaps of the split rings, the antenna radiation can be stretched in all directions due to its guiding effect, which greatly widens the half-power beamwidth of the antenna. By adding a third metallized via between the split ring and the L-shaped patch, the antenna radiation is further stretched in two diagonal directions, which further improves the half-power beamwidth of the antenna, thereby realizing communication in a wide-angle range.

[0019] (2) The wide-beam circularly polarized antenna of the present invention has a planar structure with a low profile and a very simple structure. It is easy to design and optimize, easy to process and integrate, and is conducive to achieving low cost.

[0020] (3) The wide-beam circularly polarized antenna of the present invention has a compact structure with a maximum radiation aperture of only about half a wavelength, and is easy to further expand into an array antenna structure.

[0021] (4) The height of the first metallized through hole on the two L-shaped patches of the present invention is one-quarter wavelength of the center frequency of circular polarization of the antenna. The two L-shaped patches can generate a 90° phase difference, so the antenna can achieve circular polarization.

[0022] (5) By controlling the number and position of the second metallized through-hole and / or the third metallized through-hole, the present invention can flexibly regulate the radiation of the antenna to the surroundings. Attached Figure Description

[0023] Figure 1 A three-dimensional perspective view of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna provided in an embodiment of the present invention;

[0024] Figure 2 for Figure 1 The modeling effect diagram corresponding to the three-dimensional structural schematic diagram;

[0025] Figure 3 This is a schematic diagram showing the first dielectric substrate, the second dielectric substrate, and the metal layer of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna provided in an embodiment of the present invention.

[0026] Figure 4 This is a top view of the first dielectric substrate in a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna provided in an embodiment of the present invention;

[0027] Figure 5 This is a schematic diagram of the metal layer in a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna provided in an embodiment of the present invention;

[0028] Figure 6 This is a schematic diagram of the second dielectric substrate in a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna provided in an embodiment of the present invention;

[0029] Figure 7 This is a cross-sectional view of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna provided in an embodiment of the present invention.

[0030] Figure 8 The radiation pattern of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna without a third metallized through-hole is provided in an embodiment of the present invention.

[0031] Figure 9 The radiation pattern of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna with a third metallized through-hole is provided in an embodiment of the present invention.

[0032] Figure 10 A schematic diagram of S11 parameters for a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna provided in an embodiment of the present invention;

[0033] Figure 11 A schematic diagram of the axial ratio parameters of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna provided in an embodiment of the present invention;

[0034] Figure 12 A schematic diagram of the 3-dB axial ratio beamwidth of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna at 29.6 GHz, provided for an embodiment of the present invention;

[0035] Figure 13 A schematic diagram of the 3-dB axial ratio beamwidth of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna at 30.1 GHz, provided for an embodiment of the present invention;

[0036] Figure 14 A schematic diagram of the half-power beamwidth of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna at 29.6 GHz, provided for an embodiment of the present invention.

[0037] Figure 15 A schematic diagram of the gain parameters of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna provided in an embodiment of the present invention;

[0038] Figure 16 This is a schematic diagram of the xoz plane gain pattern of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna at 28 GHz, provided in an embodiment of the present invention.

[0039] Figure 17 This is a schematic diagram of the gain pattern of a wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna at 28 GHz, provided as an embodiment of the present invention. Detailed Implementation

[0040] To make the objectives, technical solutions, and advantages of the embodiments of the present invention clearer, the technical solutions of the embodiments of the present invention will be clearly and completely described below in conjunction with the embodiments of the present invention. Obviously, the described embodiments are only some embodiments of the present invention, not all embodiments. Based on the embodiments of the present invention, all other embodiments obtained by those skilled in the art without creative effort are within the scope of protection of the present invention.

[0041] A wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna includes a first dielectric substrate 1, a metal layer 3, and a second dielectric substrate 2 stacked together. Since this invention is modeled and simulated in the high-frequency electromagnetic simulation software HFSS, the software's characteristics allow the multi-layered antenna to have a perspective effect. However, the antenna does not actually have a perspective effect; the view with a spatial perspective effect is provided merely to facilitate understanding of the design. Specifically... Figure 1 This is a three-dimensional perspective view of the antenna provided by the present invention, for a clearer demonstration. Figure 1 Spatial conditions, Figure 2 Given Figure 1 The corresponding modeling effect diagram is shown to clearly illustrate the situation of metal layer 3 and second dielectric substrate 2. Figure 3 A diagram illustrating the splitting process is provided.

[0042] The antenna employs a double-layer PCB structure, with dimensions W = 9mm and L = 9mm. The first dielectric substrate 1 is a Rogers 4003C dielectric substrate, 0.813mm thick, 9mm wide, and 9mm long, with a dielectric constant of 3.55 and a loss tangent tanδ = 0.0027. The second dielectric substrate 2 is a Rogers 5880 dielectric substrate, 0.254mm thick, 9mm wide, and 9mm long, with a dielectric constant of 2.2 and a loss tangent tanδ = 0.0009. A spatial rectangular coordinate system o-xyz is defined, comprising the origin o, x-axis, y-axis, and z-axis; both the first dielectric substrate 1 and the second dielectric substrate 2 are parallel to the xoy plane of the spatial rectangular coordinate system o-xyz.

[0043] The first dielectric substrate 1 has two rotationally symmetrical L-shaped patches 4. The L-shaped patches 4 can be considered equivalent to electric dipoles and are the main radiating structure of the antenna. Figure 4 As shown, the dimensions of the L-shaped patch 4 are W1 = 1.71 mm, L1 = 1.1 mm, and Lg = 0.75 mm.

[0044] A split ring 7 is disposed around the two L-shaped patches 4. The split ring 7 is located on the upper surface of the first dielectric substrate 1 and surrounds the two L-shaped patches 4. The split ring 7 is uniformly cut with 16 slits along the circumference. The diameter R of the split ring 7 is 4.9 mm, which is less than half the wavelength corresponding to the 29.6 GHz frequency point.

[0045] like Figure 5 As shown, the metal layer 3 is located on the lower surface of the first dielectric substrate 1. A rectangular structure is cut out from the center of the metal layer 3 to form a rectangular coupling gap 6, which is equivalent to a magnetic dipole. The length of the coupling gap 6 is Ls = 3.8 mm and the width is Ws = 0.42 mm. The two L-shaped patches 4 are connected to the metal layer 3 through a first metallized via 5. The distance g from the boundary of the first metallized via 5 to the L-shaped patch 4 is 0.12 mm. One side of the first metallized via 5 is close to the coupling gap 6 and contacts the coupling gap 6. A second metallized via 8 is provided at each gap of the split ring 7, for a total of 16, which are also rotationally symmetrical. The second metallized via 8 passes through the first dielectric substrate 1 and contacts the metal layer 3. A third metallized via 9 is provided in the gap between the L-shaped opening of the two L-shaped patches 4 and the split ring 7. The third metallized via 9 passes through the first dielectric substrate 1 and contacts the metal layer 3. The second metallized via 8 and the third metallized via 9 are via directors that further stretch the antenna's radiation in two diagonal directions, thereby further improving the antenna's half-power beamwidth.

[0046] The heights of the first metallized via 5, the second metallized via 8, and the third metallized via 9 are one-quarter of the wavelength of the antenna's circular polarization center frequency. Specifically, as shown... Figure 4 As shown, the first metallized via 5 is located in the first dielectric substrate 1, with a height of 0.813 mm and a diameter R1 = 0.45 mm. The second metallized via 8 is located in the first dielectric substrate 1, with a height of 0.813 mm and a diameter R2 = 0.24 mm. The third metallized via 9 is located in the first dielectric substrate 1, with a height of 0.813 mm and a diameter R3 = 0.25 mm. By controlling the number and position of the second metallized via 8 and / or the third metallized via 9, the radiation direction and radiation range of the antenna can be adjusted.

[0047] like Figure 6 As shown, a microstrip feed line 10 is disposed within the second dielectric substrate 2. In this embodiment, the microstrip feed line 10 is disposed on the lower surface of the second dielectric substrate 2. In practical applications, it can be disposed inside the second dielectric substrate 2 as needed. A portion of the microstrip feed line 10 is located below the coupling gap 6. The microstrip feed line 10 serves as a power feeder. The length Lk of the microstrip feed line 10 is 6.0 mm, and the width Wk is 0.6 mm.

[0048] The microstrip feed line 10 is provided with a feed port 11 at one end of the edge of the second dielectric substrate 2. Electromagnetic energy is coupled into the antenna structure through the microstrip feed line 10 and the slot structure to feed the antenna.

[0049] like Figure 7 The diagram shows a cross-sectional view of the antenna. A first dielectric substrate 1 and a second dielectric substrate 2 are placed close together (stacked together). The thickness of the first dielectric substrate 1 is h1 = 0.813 mm, and the thickness of the second dielectric substrate 2 is h2 = 0.254 mm. A metal layer 3 is tightly adhered to the lower surface of the first dielectric substrate 1, and its thickness is... Figure 7 It cannot be displayed in the image, therefore it is not shown in the diagram.

[0050] The working principle of this invention is as follows: Electromagnetic energy enters the microstrip feed line 10 through the feed port 11, is fed into the coupling slot 6, and is coupled to the first metallized via 5 through the coupling slot 6. It is then transmitted to the L-shaped patch 4 through the first metallized via 5 and radiates outwards through the L-shaped patch 4. Compared to a square patch, the L-shaped patch 4 has an additional arm, which can generate a rotating electric field. By adjusting the bandwidth and length of the arm, orthogonal currents can be achieved. The height of the first metallized via 5 in the first dielectric substrate 1 is 0.813 mm, approximately one-quarter wavelength of the circular polarization center frequency, which can generate a 90° phase difference, thus enabling the antenna to achieve circular polarization. However, the half-power beamwidth of this antenna is relatively narrow at this point.

[0051] Therefore, a split ring 7 was added around the two L-shaped patches 4 to improve the antenna's 3-dB axial ratio beamwidth. By adding a second metallized via 8 between the gaps in the split rings 7, the antenna's radiation can be stretched outwards due to its guiding effect, significantly widening the antenna's half-power beamwidth. After the above method, it was still found that the antenna's radiation was weak in one diagonal direction. Therefore, by adding a third metallized via 9 between the split rings 7 and the L-shaped patches 4 in the corresponding direction of weak radiation, the antenna's radiation was further stretched in both diagonal directions, further improving the antenna's half-power beamwidth. It is worth noting that by controlling the number and position of the second metallized via 8 and / or the third metallized via 9, the antenna's radiation in all directions can be flexibly adjusted. The antenna provided by this invention is characterized by significantly widening the half-power beamwidth of the antenna by using a simple split ring 7 and a through-hole director. It also has a wide 3-dB axial ratio beamwidth and good circular polarization characteristics. In terms of structural characteristics, it has the features of simple structure, low profile and compact structure (radiating aperture is only about half wavelength). Therefore, it has the advantages of being easy to form an array structure, and also easy to process, manufacture and integrate.

[0052] To verify the effectiveness of the present invention, the antenna of the present invention was simulated and verified. Figure 8 The radiation pattern of the antenna provided by this invention without the third metallized through-hole 9 (top view of the three-dimensional radiation pattern) shows that the radiation is weak in a diagonal direction. Figure 9 The radiation pattern of the antenna provided by this invention with the third metallized via 9 (top view of the three-dimensional radiation pattern) shows that the originally weaker radiation direction is enhanced. The third metallized via 9 is located in the originally weaker radiation direction, acting as a director to further stretch the radiation direction towards the direction where the third metallized via 9 is located. This comparison demonstrates the effectiveness of the via director in controlling the radiation pattern.

[0053] Figure 10 This is a schematic diagram of the S11 parameters of the antenna provided by the present invention. Its -10-dB bandwidth is 27.4-45.2GHz. Figure 11 This is a schematic diagram of the axial ratio parameters of the antenna provided by the present invention. Its 3-dB bandwidth is 28.6-30.4 GHz. The 3-dB axial ratio bandwidth is also the circular polarization bandwidth, indicating that the antenna can radiate electromagnetic waves in a circularly polarized manner within the 28.6-30.4 GHz bandwidth range.

[0054] Figure 12This is a schematic diagram of the 3-dB axial ratio beamwidth of the antenna provided by the present invention at 29.6 GHz. It can be observed that the 3-dB axial ratio beamwidth in the xoz plane is 172° (-82° to +90°), and the 3-dB axial ratio beamwidth in the yoz plane is 154° (-80° to +74°). Figure 13 This is a schematic diagram of the 3-dB axial ratio beamwidth of the antenna provided by the present invention at 30.1 GHz. It can be observed that the 3-dB axial ratio beamwidth in the xoz plane is 156° (-76° to +80°), and the 3-dB axial ratio beamwidth in the yoz plane is 177° (-92° to +85°). Figure 14 This diagram illustrates the half-power beamwidth of the antenna provided by this invention at 29.6 GHz. It can be observed that the half-power beamwidth in the xoz plane is 130° (-64° to +66°), and the half-power beamwidth in the yoz plane is 107° (-55° to +52°). This demonstrates that the antenna of this invention has a 3-dB axial ratio beamwidth and a wide half-power beamwidth, enabling communication over a wide angle range.

[0055] Figure 15 This is a schematic diagram of the gain parameters of the antenna provided by the present invention. A stable right-hand circular polarization gain can be observed. Figure 16 and Figure 17 These are schematic diagrams showing the gain patterns of the xoz and yoz planes at 28 GHz, respectively, provided by this invention. As can be seen from the figures, the antenna of this invention has good gain characteristics, meeting the antenna design requirements.

[0056] The above embodiments are only used to illustrate the technical solutions of the present invention, and are not intended to limit it. Although the present invention has been described in detail with reference to the foregoing embodiments, those skilled in the art should understand that modifications can still be made to the technical solutions described in the foregoing embodiments, or equivalent substitutions can be made to some of the technical features. Such modifications or substitutions do not cause the essence of the corresponding technical solutions to deviate from the spirit and scope of the technical solutions of the embodiments of the present invention.

Claims

1. A wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna, characterized in that, The device includes a first dielectric substrate, a metal layer, and a second dielectric substrate stacked together. Two rotationally symmetrical L-shaped patches are disposed on the first dielectric substrate. A split ring is disposed around the periphery of the two L-shaped patches, and the split ring is uniformly cut with several slits along its circumference. A section of the metal layer is cut away to form a coupling slit. A microstrip feed line is disposed within the second dielectric substrate. The two L-shaped patches are connected to the metal layer via a first metallized via. A second metallized via is disposed at each slit of the split ring, passing through the first dielectric substrate and contacting the metal layer. A third metallized via is disposed in the gap between the L-shaped opening of the two L-shaped patches and the split ring, passing through the first dielectric substrate and contacting the metal layer. The heights of the first, second, and third metallized vias are one-quarter wavelength of the antenna's circular polarization center frequency. The distance from the center of the first dielectric substrate to the split ring is the size of the radiating aperture, which is equal to half the wavelength corresponding to the antenna's circular polarization center frequency.

2. The wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna according to claim 1, characterized in that, The two L-shaped patches are located on the upper surface of the first dielectric substrate, the metal layer is located on the lower surface of the first dielectric substrate, and the microstrip feed line is located on the lower surface of the second dielectric substrate.

3. The wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna according to claim 1, characterized in that, The first dielectric substrate uses Rogers 4003C dielectric substrate with a dielectric constant of 3.55 and a loss tangent. =0.0027, the second dielectric substrate uses Rogers 5880 dielectric substrate with a dielectric constant of 2.2 and a loss tangent of 0.0027. =0.0009.

4. A wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna according to claim 1, characterized in that, A rectangular structure is cut out in the middle of the metal layer to form a rectangular coupling gap.

5. A wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna according to claim 1, characterized in that, The lower part of the first metallized through-hole is in contact with the coupling gap.

6. A wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna according to claim 1, characterized in that, A portion of the microstrip feeder is located below the coupling gap.

7. A wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna according to claim 1, characterized in that, The two L-shaped patches are equivalent to electric dipoles, and the coupling gap is equivalent to a magnetic dipole.

8. A wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna according to claim 1, characterized in that, The microstrip feed line has a feed port at one end of the edge of the second dielectric substrate, and electromagnetic energy is coupled into the antenna from the feed port.

9. A wide-beam millimeter-wave circularly polarized magnetoelectric dipole antenna according to claim 1, characterized in that, The radiation direction and radiation range of the antenna can be adjusted by controlling the number and position of the second and / or third metallized vias.

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