A method and apparatus for correcting for co-resonant IQ imbalance

Abstract

The application provides a co-resonance IQ imbalance coupling correction method and device, a binary first-order evaluation coefficient equation group is constructed by introducing variables through a phase shifter change to decouple the coupling problems of TX image / direct current and ORX image / direct current or, the image and LO leakage problems in a TDD large bandwidth scene can be solved on the digital side, RX or feedback mixer devices can be saved, the performance is stable, and the reliability is strong. The application is mainly applied in the fields of small base stations, MIMO macro base stations or enterprise-level WIFI.

Description

TECHNICAL FIELD

[0001] The present application relates to the technical field of wireless communication, in particular to a common resonance IQ imbalance coupling correction method and device. BACKGROUND

[0002] Increasing demand for high-speed broadband services requires wireless communication systems to adopt higher spectral efficiency and wider bandwidth. With the evolution of the fifth generation of wireless mobile networks, it has become an industry trend to use higher order modulation and multi-channel aggregation for wireless backhaul. In fact, low-cost microwave backhaul systems usually use in-phase (I) / quadrature (Q) modulation architecture for up-conversion and channelization. This architecture consists of two mixers with the same carrier frequency of the orthogonal local oscillator (LO). The implementation of the I / Q modulation architecture requires the installation of two digital-to-analog converters (D / A) and two analog-to-digital converters (A / D) in the transmitter (Tx) and receiver (Rx or ORx, mainly described below as feedback ORx), respectively. There is also a low-pass filter in each I and Q branch of the Tx or ORx for signal reconstruction or anti-aliasing. Any variation between components in the I and Q branches will cause I / Q imbalance, which will hinder the engineering of high-order modulation. Therefore, analog I / Q modulation is still the mainstream low-cost radio architecture, and I / Q imbalance compensation is usually implemented in the digital signal processing chain.

[0003] However, the I / Q imbalance of Tx and ORx blocks the use of some typical industrial scenarios. For example, in a receiving system, in order to improve capacity and reduce cost, the I / Q imbalance at Tx must be pre-compensated to eliminate the interference of the channel so that each channel can meet the strict demodulation requirements. For most communication systems including MIMO, I / Q imbalance estimation should be performed locally on the digital side. In addition, due to the wider bandwidth (more than 200MHz) of the communication system, the frequency dependence of I / Q imbalance should be considered.

[0004] Separating Tx and ORx I / Q imbalance is quite challenging because the signal received by the ORX can only see the overall impact of the Tx and ORx I / Q imbalance. In general, two unknowns cannot be found from one observation unless other independent variables cause changes in the observation. Many current technologies are only used to independently estimate ORx I / Q imbalance or estimate TX I / Q imbalance, and most solutions are to compensate for I / Q imbalance on the receiver and pre-compensate Tx I / Q imbalance on the transmitter. The estimation method of the coefficient is independently solved in the time and frequency domains, and both depend on the fact that the frequency points of the TX mixer and the feedback mixer are not completely consistent to independently estimate the TX I / Q imbalance or the ORX I / Q imbalance. The above solutions cannot solve the mirror coupling problem under the condition that the TX mixer and the feedback or RX mixer have the same frequency point.

[0005] Therefore, how to provide a method capable of distinguishing the transmission and feedback mirror image / dc coupling under the correction co-resonant frequency point is a problem to be solved at present. SUMMARY

[0006] In order to improve the above problems, the present application provides a co-resonant IQ imbalance coupling correction method and device.

[0007] The first aspect of the embodiment of the present application provides a co-resonant IQ imbalance coupling correction method, which comprises:

[0008] After power-on initialization, the angle of the loop phase shifter is initialized to a first phase value;

[0009] The carrier service signal is established, the transmission data and the feedback loopback data delay are aligned, and the first loop gain is calculated;

[0010] According to the transmission data and the feedback loopback data after delay alignment, the first mirror estimation compensation coefficient is calculated;

[0011] The angle of the loop phase shifter is controlled to a second phase value, which is at least greater than the first phase value by more than 5 degrees;

[0012] Under the condition that the carrier service signal does not change, the transmission data and the feedback loopback data delay are aligned again, and the second loop gain is calculated;

[0013] According to the transmission data and the feedback loopback data after delay alignment, the second mirror estimation compensation coefficient is calculated;

[0014] The transmission mirror compensation coefficient and the feedback mirror compensation coefficient are calculated according to the first calculated mirror compensation coefficient and the second calculated mirror compensation coefficient;

[0015] The calculated transmission mirror compensation coefficient and the feedback mirror compensation coefficient are written into the corresponding compensation filter structure.

[0016] Optionally, the step of calculating the first mirror estimation compensation coefficient according to the transmission data and the feedback loopback data after delay alignment specifically comprises:

[0017] According to the formula

[0018]

[0019] The first mirror estimation compensation coefficient c0 is calculated;

[0020] The step of calculating the second mirror estimation compensation coefficient according to the transmission data and the feedback loopback data after delay alignment specifically comprises:

[0021] According to the formula

[0022]

[0023] calculating a second mirror estimation compensation coefficient c1;

[0024] Wherein, fb0(n) is a feedback signal of the phase shifter converted to a first phase value, fb1(n) is a feedback signal of the phase shifter converted to a second phase value, the feedback signal contains transmission mirror information and feedback mirror information; x(n) signal is a baseband ideal modeling signal.

[0025] Optionally, the step of calculating the transmission mirror compensation coefficient and the feedback mirror compensation coefficient according to the first calculated mirror compensation coefficient and the second calculated mirror compensation coefficient specifically comprises:

[0026] According to the first mirror estimation compensation coefficient and the second mirror estimation compensation coefficient, a binary first-order equation group is constructed

[0027]

[0028] Solving the equation group, the transmission mirror compensation coefficient f and the feedback mirror compensation coefficient h are obtained.

[0029] Wherein, G0=g0 / conj(g0), G1=g1 / conj(g1), g0 is a first loop gain, and g1 is a second loop gain.

[0030] Optionally, the method further comprises:

[0031] The transmission mirror compensation coefficient and the feedback mirror compensation coefficient are repeatedly calculated at a certain period until the compensation performance of the compensation filter meets the preset requirement.

[0032] The second aspect of the embodiment of the application provides a common local oscillator IQ imbalance coupling correction device, the device comprises:

[0033] The phase shift control unit is used to initialize the angle of the loop phase shifter to a first phase value after power-on initialization.

[0034] The gain calculation unit is used to establish a carrier service signal, align transmission data and feedback loopback data delay, and calculate a first loop gain.

[0035] The compensation calculation unit is used to calculate a first mirror estimation compensation coefficient according to the transmission data and the feedback loopback data after delay alignment.

[0036] The phase shift control unit is also used to control the angle of the loop phase shifter to a second phase value, and the second phase value is at least greater than the first phase value by more than 5 degrees.

[0037] The gain calculation unit is further configured to, when the carrier service signal does not change, perform again the time delay alignment of the transmission data and the feedback loopback data, and calculate a second loop gain;

[0038] The compensation calculation unit is further configured to calculate a second mirror estimation compensation coefficient according to the transmission data and the feedback loopback data after the time delay alignment.

[0039] The compensation calculation unit is further configured to calculate a transmission mirror compensation coefficient and a feedback mirror compensation coefficient according to the first calculated mirror compensation coefficient and the second calculated mirror compensation coefficient.

[0040] The coefficient writing unit is configured to write the calculated transmission mirror compensation coefficient and the feedback mirror compensation coefficient into corresponding compensation filter structures.

[0041] Optionally, the compensation calculation unit is specifically configured to:

[0042] According to a formula

[0043]

[0044] Calculate a first mirror estimation compensation coefficient c0.

[0045] According to a formula

[0046]

[0047] Calculate a second mirror estimation compensation coefficient c1.

[0048] Wherein, fb0(n) is a feedback signal whose phase is converted to a first phase value by a phase shifter, fb1(n) is a feedback signal whose phase is converted to a second phase value by a phase shifter, the feedback signal contains transmission mirror information and feedback mirror information; x(n) is a baseband ideal modeling signal.

[0049] Optionally, the compensation calculation unit is further specifically configured to:

[0050] According to the first mirror estimation compensation coefficient and the second mirror estimation compensation coefficient, construct a binary first-order equation group

[0051]

[0052] Solve the equation group to obtain a transmission mirror compensation coefficient f and a feedback mirror compensation coefficient h.

[0053] Wherein, G0=g0 / conj(g0), G1=g1 / conj(g1), g0 is a first loop gain, and g1 is a second loop gain.

[0054] Optionally, the apparatus further comprises:

[0055] The timing polling unit is configured to poll repeatedly the calculation of the transmitting mirror image compensation coefficient and the feedback mirror image compensation coefficient at a certain period until the compensation performance of the compensation filter meets the preset requirement.

[0056] In a third aspect, the present application provides an electronic device, comprising:

[0057] one or more processors; a memory; one or more application programs, wherein the one or more application programs are stored in the memory and configured to be executed by the one or more processors, and the one or more programs are configured to execute the method according to the first aspect.

[0058] In a fourth aspect, the present application provides a computer readable storage medium, wherein the computer readable storage medium stores program codes, and the program codes can be invoked by a processor to execute the method according to the first aspect.

[0059] To sum up, the present application provides a co-resonant IQ imbalance coupling correction method and device, electronic equipment and storage medium, which introduces variables by changing the phase shifter to construct a binary first-order evaluation coefficient equation set to decouple the coupling problem of TX mirror / DC and ORX mirror / DC or, can solve the mirror and LO leakage problem in the TDD large bandwidth scene on the digital side, can save RX or feedback mixer devices, has stable performance and strong reliability. It is mainly applied in small base stations or MIMO macro base stations or enterprise-level WIFI fields. BRIEF DESCRIPTION OF DRAWINGS

[0060] In order to more clearly illustrate the technical solutions of the embodiments of the present application, the following will briefly introduce the drawings needed to be used in the embodiments. It should be understood that the following drawings only show some embodiments of the present application, and therefore should not be regarded as a limitation on the scope. For those skilled in the art, other related drawings can also be obtained without creative labor on the basis of these drawings.

[0061] Figure 1 Problem solved by the co-resonant IQ imbalance coupling correction method of the present application embodiment;

[0062] Figure 2 Method flowchart of the co-resonant IQ imbalance coupling correction method of the present application embodiment;

[0063] Figure 3 Transmitting mirror image uncorrected result graph and pre-distortion mirror image graph after calculating compensation coefficient f of the present application embodiment;

[0064] Figure 4 Feedback mirror image correction result graph of the present application embodiment.

[0065] Figure 5 A function module block diagram of the co-resonant IQ imbalance coupling correction device of the embodiment of the present application;

[0066] Figure 6 A structure block diagram of the electronic device for performing the co-resonant IQ imbalance coupling correction method according to the embodiment of the present application.

[0067] Figure 7 A structure block diagram of the computer readable storage medium for storing or carrying the program code for implementing the co-resonant IQ imbalance coupling correction method according to the embodiment of the present application.

[0068] Reference signs:

[0069] Phase shift control unit 110; gain calculation unit 120; compensation calculation unit 130; coefficient writing unit 140; timing polling unit 150; electronic device 300; processor 310; memory 320; computer readable storage medium 400; program code 410. DETAILED DESCRIPTION

[0070] Increasing demand for high-speed broadband services requires wireless communication systems to employ higher spectral efficiency and wider bandwidth. With the evolution of wireless mobile networks to the fifth generation, it has become an industry trend to use higher order modulation and multi-channel aggregation for wireless backhaul. In fact, low-cost microwave backhaul systems usually use in-phase (I) / quadrature (Q) modulation architecture for up-conversion and channelization. This architecture consists of two mixers with quadrature local oscillator (LO) subcarriers of the same carrier frequency. The implementation of the I / Q modulation architecture requires the installation of two digital-to-analog converters (D / A) and two analog-to-digital converters (A / D) in the transmitter (Tx) and receiver (Rx or ORx, hereinafter mainly described as feedback ORx), respectively. There is also a low-pass filter in each I and Q branch of the Tx or ORx for signal reconstruction or anti-aliasing. Any variation between components in the I and Q branches will cause I / Q imbalance, which will hinder the engineering of high-order modulation. Therefore, analog I / Q modulation is still the mainstream low-cost radio architecture, and I / Q imbalance compensation is usually implemented in the digital signal processing chain.

[0071] However, the I / Q imbalance of Tx and ORx blocks the mirror from being used in some typical industrial scenarios. For example, in a receiving system, in order to improve capacity and reduce cost, the I / Q imbalance at Tx must be pre-compensated to eliminate the interference of channels so that each channel can meet the strict demodulation requirements. For most communication systems including MIMO, the I / Q imbalance estimation should be performed locally at the digital side. In addition, due to the wider bandwidth (more than 200 MHz) of the communication system, the frequency dependence of the I / Q imbalance should be considered.

[0072] It is quite challenging to separate the Tx and ORx I / Q imbalance because the signal received by the ORx can only see the overall effect caused by the Tx and ORx I / Q imbalance. Generally, two unknowns cannot be found from one observation unless other independent variables cause the change of the observation. At present, many technologies are only used to independently estimate the ORx I / Q imbalance or the Tx I / Q imbalance, and most solutions are to compensate for the I / Q imbalance at the receiver and pre-compensate for the Tx I / Q imbalance at the transmitter. The estimation methods of the coefficients are independently solved in the time domain and the frequency domain, and both depend on the fact that the frequency points of the TX mixer and the feedback mixer are not completely consistent to independently estimate the Tx I / Q imbalance or the ORx I / Q imbalance. The above solutions cannot solve the mirror coupling problem under the condition that the TX mixer and the feedback or RX mixer have the same frequency point.

[0073] Therefore, how to provide a more accurate and effective co-resonance IQ imbalance coupling correction method is a problem to be solved at present.

[0074] In view of this, the designer of the present application considers introducing variables by changing the phase shifter to construct a binary first-order evaluation coefficient equation set to decouple the coupling problem of the TX mirror / dc and the ORX mirror / dc or the coupling problem of the TX mirror / dc and the ORX dc. The method provided by the present application is mathematically rigorous, good in performance, strong in stability, and has strong engineering implementation value.

[0075] To make the purpose, technical solutions and advantages of the embodiments of the present application clearer, the technical solutions in the embodiments of the present application will be described clearly and completely below with reference to the drawings in the embodiments of the present application. Obviously, the described embodiments are only a part of the embodiments of the present application, not all the embodiments. The components of the embodiments of the present application described and shown in the drawings can be arranged and designed in various different configurations.

[0076] Therefore, the following detailed description of the embodiments of the present application provided in the drawings is not intended to limit the scope of the claimed present application, but only represents selected embodiments of the present application. All other embodiments obtained by those of ordinary skill in the art without creative labor based on the embodiments in the present application belong to the scope of protection of the present application.

[0077] It should be noted that similar reference numerals and letters refer to like items throughout the accompanying drawings, and once an item is defined in one drawing, it is not necessary to further define and explain it in subsequent drawings.

[0078] In the description of the present application, it should be noted that the terms "top", "bottom", "inner", "outer" and the like indicate the orientation or positional relationship based on the orientation or positional relationship shown in the drawings, or the orientation or positional relationship when the product of the application is usually placed, and are only for the convenience of describing the application and simplifying the description, and therefore cannot be understood as indicating or implying that the indicated device or element must have a particular orientation, be constructed and operated in a particular orientation, and therefore cannot be understood as limiting the application. In addition, the terms "first", "second" and the like are only used to distinguish the description and cannot be understood as indicating or implying relative importance.

[0079] In the description of the present application, it should be noted that unless otherwise explicitly specified and limited, the terms "set", "mount", "connected", "connected" should be broadly understood, for example, it can be fixedly connected, or it can be detachably connected, or integrally connected, it can be mechanically connected, or it can be electrically connected, it can be directly connected, or indirectly connected through an intermediate medium, or it can be the communication between two elements. For those skilled in the art, the specific meaning of the above terms in the present application can be understood according to the specific circumstances.

[0080] It should be noted that the embodiments in the present application and the features in the embodiments can be combined with each other without conflict.

[0081] From the analysis of signal correlation characteristics, the mirror image generated by the transmit channel and the mirror image generated by the feedback ORX channel will be completely coupled in the feedback digital side signal under the common LO frequency point scene, and the two mirror image information has strong correlation, and cannot effectively distinguish the transmit mirror image component information and the feedback mirror image component information from the mirror image of the ORX receive signal, Figure 1 The phenomenon is shown in the following.

[0082] Please refer to Figure 2 In order to solve the mirror image coupling problem in the TX and ORX common frequency point scene in the above problem, the present embodiment provides a common resonant IQ imbalance coupling correction method, which comprises the following steps:

[0083] Step S101, after power-on initialization, the angle of the loop phase shifter is initialized to a first phase value.

[0084] First, the initialization of the application environment is completed, and the first phase value of the loop phase shifter initialization is degrees.

[0085] Step S102, establish a carrier service signal, perform transmission data and feedback loopback data delay alignment, and calculate a first loop gain g0.

[0086] The method for calculating the first loop gain g0may adopt an existing loop gain calculation method.

[0087] Step S103, according to the transmission data and the feedback loopback data after delay alignment, calculate a first mirror estimation compensation coefficient c0.

[0088] The step of calculating the first mirror estimation compensation coefficient can adopt an LMS algorithm, and the specific calculation method comprises:

[0089] According to the formula

[0090]

[0091] Calculate the first mirror estimation compensation coefficient c0.

[0092] Wherein, fb0(n) is a feedback signal whose phase is converted to a first phase value by a phase shifter, fb1(n) is a feedback signal whose phase is converted to a second phase value by a phase shifter, the feedback signal contains transmission mirror information and feedback mirror information; x(n) is a baseband ideal modeling signal

[0093] Steps S102-S103 are to verify the stability of the transmission and ORX feedback environment, and at the same time, to obtain the delay gain alignment of the transmission data and the ORX data, and to obtain The angle gain compensation value and the modeling error on which the coefficient calculation c0depends.

[0094] Step S104, control the angle of the loop phase shifter to a second phase value, which is at least 5 degrees larger than the first phase value.

[0095] When adjusting the angle of the loop phase shifter, it is required that the second adjustment of the phase shifter angle is at least 5 degrees larger than the initial angle .

[0096] Step S105, under the condition that the carrier service signal does not change, perform transmission data and feedback loopback data delay alignment again, and calculate a second loop gain.

[0097] The method for calculating the second loop gain g1may adopt the same calculation method as g0.

[0098] Step S106, according to the transmission data and the feedback loopback data after delay alignment, calculate a second mirror estimation compensation coefficient c1.

[0099] The second mirror estimation compensation coefficient c1 can also be calculated by using the LMS algorithm, and the specific calculation method includes:

[0100] According to the formula

[0101]

[0102] The second mirror estimation compensation coefficient c1 is calculated.

[0103] Wherein, fb1(n) is the feedback signal of the phase shifter converted to the second phase value.

[0104] Steps S104-S106 achieve the purpose of steps S101-S103, and the second group of calculation data after phase shifting is obtained. Due to the existence of the phase shifter, it can be considered that there is a deviation between the two times of phase generated mirror.

[0105] In step S107, the transmission mirror compensation coefficient and the feedback mirror compensation coefficient are calculated according to the first calculation mirror compensation coefficient and the second calculation mirror compensation coefficient.

[0106] For the calculation of the transmission mirror compensation coefficient f and the feedback mirror compensation coefficient h, a simultaneous equation set is used for solving, and the specific method is as follows:

[0107] According to the first mirror estimation compensation coefficient and the second mirror estimation compensation coefficient, a binary linear equation set is constructed

[0108]

[0109] The transmission mirror compensation coefficient f and the feedback mirror compensation coefficient h are obtained by solving the equation set.

[0110] Wherein, G0=g0 / conj(g0), G1=g1 / conj(g1).

[0111] In step S108, the calculated transmission mirror compensation coefficient and the feedback mirror compensation coefficient are written into the corresponding compensation filter structure.

[0112] As a preferred embodiment of the embodiment of the present application, the method provided by the embodiment of the present application further includes:

[0113] The calculation of the transmission mirror compensation coefficient and the feedback mirror compensation coefficient is repeated by polling at a certain period until the compensation performance of the compensation filter meets the preset requirement.

[0114] Through the above steps S101-S108, the compensation performance of the compensation filter may not meet the preset requirement.

[0115] After step S108 is executed, step S109 is needed to be executed to judge whether the compensation performance of the compensation filter meets the preset requirement. If the compensation performance does not meet the preset requirement, the above steps S102-S108 are repeatedly executed until the compensation performance of the compensation filter meets the preset requirement.

[0116] The following will be described by a specific example:

[0117] In the embodiment, the test signal is NR100M, the test downlink frequency point is 1.8G, the carrier frequency point is 1.75GHz, the Transceiver chip adopts BZ20, the chip is a TDD scene special chip, and the transmission mirror and the feedback ORX mirror are coupled. The following experiment takes the correction of distinguishing the transmission mirror and the ORX feedback mirror as an example. The process of the common resonant IQ imbalance coupling correction method is as follows:

[0118] S1: test environment initialization, set the initial phase of the peripheral phase shifter to 0°, and observe the BZ20 downlink air interface mirror performance by sending out the cell carrier service signal; S2: the air interface signal is looped back to the digital logic side through BZ20-ORX, the TX transmission signal and the feedback signal are sampled to the software, the software realizes the time delay alignment of the transmission data and the feedback loopback data, and the loop gain g0 is calculated; S3: according to the transmission data and the feedback loopback data after time delay alignment, the software calculates the mirror estimation compensation coefficient c0 by using the LMS algorithm; S4: at this time, the cell carrier service signal is unchanged, and the software controls the external analog phase shifter to shift by 90° by means of register configuration; S5: the TX transmission signal and the feedback signal are sampled to the software, the software realizes the time delay alignment of the transmission data and the feedback loopback data, and the loop gain g1 is calculated; S6: according to the transmission data and the feedback loopback data after time delay alignment, the software calculates the mirror estimation compensation coefficient c1 by using the LMS algorithm; S7: the software calculates the transmission mirror compensation coefficient f and the feedback mirror compensation coefficient h according to g0, c0, g1 and c1; S8: the software configures the decomposed coefficients to the digital logic compensation structure; S9: the software polls and repeats S2-S8 until the performance meets the requirement. When the above formula is used for calculation in S3 and S6, the fb0(n) and fb1(n) signals are the feedback signals after the phase shifter converts the phase by 0° and 90°, and the x(n) signal is the baseband NR100M signal. The correction effect is as shown in the following table: Figure 3-4

[0119] ​In conclusion, the application provides a co-resonance IQ imbalance coupling correction method, which introduces variables by phase shifter changes to construct a binary first-order evaluation coefficient equation set to decouple the coupling problems of TX image / DC and ORX image / DC or, can solve the image and LO leakage problems in the TDD large bandwidth scene on the digital side, can save RX or feedback mixer devices, has stable performance and strong reliability. It is mainly applied in the fields of small base stations or MIMO macro base stations or enterprise-level WIFI.

[0120] As Figure 5 shown, the co-resonance IQ imbalance coupling correction device provided by the application implementation includes:

[0121] The phase shift control unit 110 is used for initializing the angle of the loop phase shifter to a first phase value after power-on initialization;

[0122] The gain calculation unit 120 is used for establishing a carrier service signal, performing time delay alignment of transmission data and feedback loopback data, and calculating a first loop gain;

[0123] The compensation calculation unit 130 is used for calculating a first image estimation compensation coefficient according to the time-delay-aligned transmission data and feedback loopback data;

[0124] The phase shift control unit 110 is also used for controlling the angle of the loop phase shifter to a second phase value, which is at least 5 degrees larger than the first phase value;

[0125] The gain calculation unit 120 is also used for, without changing the carrier service signal, performing time delay alignment of transmission data and feedback loopback data again, and calculating a second loop gain;

[0126] The compensation calculation unit 130 is also used for calculating a second image estimation compensation coefficient according to the time-delay-aligned transmission data and feedback loopback data;

[0127] The compensation calculation unit 130 is also used for calculating transmission image compensation coefficients and feedback image compensation coefficients according to the first calculated image compensation coefficient and the second calculated image compensation coefficient;

[0128] The coefficient writing unit 140 is used for writing the calculated transmission image compensation coefficients and feedback image compensation coefficients into corresponding compensation filter structures.

[0129] As a preferred embodiment of the present embodiment, the compensation calculation unit 130 is specifically used for:

[0130] According to the formula

[0131]

[0132] calculate a first mirror estimation compensation coefficient c0;

[0133] According to the formula

[0134]

[0135] calculate a second mirror estimation compensation coefficient c1;

[0136] Wherein, fb0(n) is the feedback signal of the phase shifter converted to the first phase value, fb1(n) is the feedback signal of the phase shifter converted to the second phase value, the feedback signal contains the transmit mirror information and the feedback mirror information; x(n) signal is the baseband ideal modeling signal.

[0137] As a preferred embodiment of the present embodiment, the compensation calculation unit 130 is also specifically used for:

[0138] According to the first mirror estimation compensation coefficient and the second mirror estimation compensation coefficient, a binary first-order equation group is constructed

[0139]

[0140] Solving the equation group, the transmit mirror compensation coefficient f and the feedback mirror compensation coefficient h are obtained.

[0141] Wherein, G0=g0 / conj(g0), G1=g1 / conj(g1), g0 is the first loop gain, and g1 is the second loop gain.

[0142] As a preferred embodiment of the present embodiment, the device further comprises:

[0143] The timing polling unit 150 is used for polling repeatedly calculating the transmit mirror compensation coefficient and the feedback mirror compensation coefficient at a certain period until the compensation performance of the compensation filter meets the preset requirement.

[0144] The common resonance IQ imbalance coupling correction device provided by the embodiment of the present application is used for implementing the common resonance IQ imbalance coupling correction method described above, and therefore the specific implementation manner is the same as the above method, which will not be described here again.

[0145] As shown in Figure 6 A structural block diagram of an electronic device 300 provided by an embodiment of the present application is shown in the figure. The electronic device 300 can be a smart phone, a tablet computer, an electronic book, or the like, which can run an application program. The electronic device 300 in the present application can include one or more of the following components: a processor 310, a memory 320, and one or more application programs, wherein the one or more application programs can be stored in the memory 320 and configured to be executed by the one or more processors 310, and the one or more programs are configured to execute the method as described in the foregoing method embodiment.

[0146] Processor 310 may include one or more processing cores. Processor 310 connects to various parts within the electronic device 300 using various interfaces and lines, and performs various functions and processes data of the electronic device 300 by running or executing instructions, programs, code sets, or instruction sets stored in memory 320, and by calling data stored in memory 320. Optionally, processor 310 may be implemented using at least one hardware form of Digital Signal Processing (DSP), Field-Programmable Gate Array (FPGA), or Programmable Logic Array (PLA). Processor 310 may integrate one or a combination of several of the following: Central Processing Unit (CPU), Graphics Processing Unit (GPU), and modem. The CPU primarily handles the operating system, user interface, and applications; the GPU is responsible for rendering and drawing the displayed content; and the modem handles wireless communication. It is understood that the modem may also not be integrated into processor 310 and may be implemented separately using a communication chip.

[0147] The memory 320 may include random access memory (RAM) or read-only memory (ROM). The memory 320 can be used to store instructions, programs, code, code sets, or instruction sets. The memory 320 may include a program storage area and a data storage area. The program storage area may store instructions for implementing an operating system, instructions for implementing at least one function (such as touch functionality, sound playback functionality, image playback functionality, etc.), and instructions for implementing the various method embodiments described below. The data storage area may also store data created by the terminal during use (such as phonebook data, audio and video data, chat log data, etc.).

[0148] like Figure 7 The diagram shows a structural block diagram of a computer-readable storage medium 400 provided in an embodiment of the present invention. The computer-readable medium stores program code 410, which can be called by a processor to execute the methods described in the above method embodiments.

[0149] The computer-readable storage medium 400 can be an electronic memory such as a flash memory, an EEPROM (electrically erasable programmable read-only memory), an EPROM, a hard disk or a ROM. Optionally, the computer-readable storage medium 400 comprises a non-transitory computer-readable medium. The computer-readable storage medium 400 has storage space for program codes 410 for performing any of the method steps described above. These program codes 410 can be read from or written to one or more computer program products. The program codes 410 can be compressed, for example, in a suitable form.

[0150] In summary, the present application provides a co-resonant IQ imbalance correction method and device, electronic equipment and storage medium. The coupling problem of TX image / DC and ORX image / DC or is decoupled by introducing variables through phase shifter changes to construct a binary first-order evaluation coefficient equation set, which can solve the image and LO leakage problem in the TDD large bandwidth scenario on the digital side, can save RX or feedback mixer devices, has stable performance and strong reliability. It is mainly applied in small base stations or MIMO macro base stations or enterprise-level WIFI fields.

[0151] In several embodiments disclosed in the present application, it should be understood that the disclosed devices and methods can also be implemented in other ways. The device embodiments described above are only schematic, for example, the flowcharts and block diagrams in the drawings show the possible implementation architectures, functions and operations of the devices, methods and computer program products according to the embodiments of the present application. In this regard, each block in the flowchart or block diagram can represent a module, a program segment or a part of code, which contains one or more executable instructions for implementing the specified logical function. It should also be noted that in some alternative implementations, the functions noted in the blocks can occur in different orders from that shown in the drawings. For example, two consecutive blocks can actually be executed substantially in parallel, and sometimes they can be executed in reverse order, depending on the functions involved. It should also be noted that each block in the block diagram and / or flowchart, and the combination of blocks in the block diagram and / or flowchart, can be implemented by a dedicated hardware-based system for performing the specified functions or actions, or can be implemented by a combination of dedicated hardware and computer instructions.

[0152] In addition, the functional modules in each embodiment of the present application can be integrated together to form an independent part, or each module can exist independently, or two or more modules can be integrated to form an independent part.

[0153] If the functions are implemented in the form of software function modules and sold or used as independent products, the functions can be stored in a computer readable storage medium. Based on this understanding, the technical solutions of the present application essentially or the parts that contribute to the prior art or parts of the technical solutions can be embodied in the form of a software product. The computer software product is stored in a storage medium and includes a number of instructions for causing a computer device (which can be a personal computer, a server, or a network device, etc.) to execute all or part of the steps of the methods described in the various embodiments of the present application. The aforementioned storage medium includes: a U disk, a mobile hard disk, a read-only memory (ROM, Read-Only Memory), a random access memory (RAM, Random Access Memory), a magnetic disk or an optical disk, and various media that can store program codes.

Claims

1. A common-oscillator IQ unbalanced coupling correction method, characterized in that, The method includes: After power-on initialization, initialize the loop phase shifter angle to the first phase value; Establish a carrier service signal, align the time delays of transmitted data and feedback loopback data, and calculate the first loop gain; Calculate the first image estimation compensation coefficient based on the time-delay aligned transmission data and feedback loopback data; The angle of the loop phase shifter is controlled to a second phase value, the second phase value being at least 5 degrees greater than the first phase value; Without changing the carrier service signal, the transmission data and feedback loopback data delays are aligned again, and the second loop gain is calculated. The second mirror estimation compensation coefficient is calculated based on the time-delay aligned transmission data and feedback loop data. Calculate the transmit image compensation coefficient and the feedback image compensation coefficient based on the first image estimation compensation coefficient and the second image estimation compensation coefficient; The calculated projection image compensation coefficients and feedback image compensation coefficients are written into the corresponding compensation filter structure.

2. The common-oscillator IQ unbalanced coupling correction method according to claim 1, characterized in that, The step of calculating the first image estimation compensation coefficient based on the time-delay aligned transmit data and feedback loopback data specifically includes: According to the formula Calculate the first mirror estimation compensation coefficient c0; The step of calculating the second mirror estimation compensation coefficient based on the time-delay aligned transmit data and feedback loopback data specifically includes: According to the formula Calculate the second mirror estimation compensation coefficient c1; in, fb 0 (n) This is the feedback signal for the phase shifter to switch to the first phase value. fb 1 (n) The feedback signal is used to convert the phase of the phase shifter to the second phase value. The feedback signal contains transmit image information and feedback image information. x(n) The signal is a baseband ideal modeling signal.

3. The common-oscillator IQ unbalanced coupling correction method according to claim 2, characterized in that, The step of calculating the transmit image compensation coefficient and the feedback image compensation coefficient based on the first image estimation compensation coefficient and the second image estimation compensation coefficient specifically includes: A system of two linear equations is constructed based on the first and second mirror estimation compensation coefficients. Solving the system of equations yields the transmit image compensation coefficients. f and feedback mirror compensation coefficient h ; in, , g0 is the first loop gain, and g1 is the second loop gain.

4. The common-oscillator IQ unbalanced coupling correction method according to claim 3, characterized in that, The method further includes: The transmit image compensation coefficient and the feedback image compensation coefficient are repeatedly calculated in a polling cycle until the compensation performance of the compensation filter meets the preset requirements.

5. A common-local oscillator IQ unbalanced coupling correction device, characterized in that, The device includes: The phase shift control unit is used to initialize the angle of the loop phase shifter to the first phase value after power-on initialization. The gain calculation unit is used to establish the carrier service signal, perform time delay alignment of transmitted data and feedback loopback data, and calculate the first loop gain. The compensation calculation unit is used to calculate the first image estimation compensation coefficient based on the time-delay aligned transmit data and feedback loopback data; The phase shift control unit is also used to control the angle of the loop phase shifter to a second phase value, wherein the second phase value is at least 5 degrees greater than the first phase value; The gain calculation unit is also used to perform time delay alignment of transmitted data and feedback loopback data again and calculate the second loop gain without changing the carrier service signal; The compensation calculation unit is also used to calculate the second mirror estimation compensation coefficient based on the time-delay aligned transmission data and feedback loopback data; The compensation calculation unit is further configured to calculate the transmission image compensation coefficient and the feedback image compensation coefficient based on the first image estimation compensation coefficient and the second image estimation compensation coefficient. The coefficient writing unit is used to write the calculated projection image compensation coefficients and feedback image compensation coefficients into the corresponding compensation filter structure.

6. The common-oscillator IQ unbalanced coupling correction device according to claim 5, characterized in that, The compensation calculation unit is specifically used for: According to the formula Calculate the first mirror estimation compensation coefficient c0; According to the formula Calculate the second mirror estimation compensation coefficient c1; in, fb 0 (n) This is the feedback signal for the phase shifter to switch to the first phase value. fb 1 (n) The feedback signal is used to convert the phase of the phase shifter to the second phase value. The feedback signal contains transmit image information and feedback image information. x(n) The signal is a baseband ideal modeling signal.

7. The common-oscillator IQ unbalanced coupling correction device according to claim 6, characterized in that, The compensation calculation unit is also specifically used for: A system of two linear equations is constructed based on the first and second mirror estimation compensation coefficients. Solving the system of equations yields the transmit image compensation coefficients. f and feedback mirror compensation coefficient h ; in, , g0 is the first loop gain, and g1 is the second loop gain.

8. The common-oscillator IQ unbalanced coupling correction device according to claim 7, characterized in that, The device further includes: The timed polling unit is used to repeatedly calculate the transmit image compensation coefficient and the feedback image compensation coefficient at a certain period until the compensation performance of the compensation filter meets the preset requirements.

9. An electronic device, characterized in that, include: One or more processors; Memory; One or more applications, wherein the one or more applications are stored in the memory and configured to be executed by the one or more processors, the one or more applications being configured to perform the method as described in any one of claims 1-4.

10. A computer-readable storage medium, characterized in that, The computer-readable storage medium stores program code that can be invoked by a processor to execute the method as described in any one of claims 1-4.

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