Power transmission system and method

Abstract

The invention relates to a solar panel system for providing power to an AC or DC load, comprising a plurality of photovoltaic cells and corresponding high frequency power modules that can be phase locked to the frequency of any AC power signal present in the load. The system or circuit has a single aggregator for collecting AC or DC power signals originating from the photovoltaic cells via the high frequency power module and high frequency link system. Power transfer in the high frequency link system may be by wired, wireless, or near field bimodal wireless power transfer. The photovoltaic cells are disposed facing downward on a planar transparent solar cover and a printed circuit board carrying circuitry for the high frequency power module is mounted facing upward. The mounted device is conformally encapsulated with a protective polymer cover. A method for encapsulating the photovoltaic cell and its associated high frequency power module together on the planar transparent solar cover is provided.

Description

[0001] CROSS REFERENCE TO RELATED APPLICATIONS

[0002] This application claims priority to and the benefit of U.S. Application No. 63 / 379,547, filed on October 14, 2022, and U.S. Application No. 63 / 476,781, filed on December 22, 2022, the contents of each of which are incorporated herein by reference in their entirety for all purposes. Technical Field

[0003] The present invention relates to a power transmitter, a receiver, and a system and method for power transmission. Background Art

[0004] In inductive power transfer (IPT), power is typically transferred between coils by means of a magnetic field. An alternating current (AC) is driven through a transmitter coil to form an oscillating magnetic field. The magnetic field passes through a receiving coil, where it induces an AC current in the receiving coil. The induced AC current can drive a load directly, or be rectified to a direct current (DC), which is applied to drive a load. To achieve high efficiency, the transmitter and receiver coils must be very close together. For example, typically, the transmitter and receiver coils are separated by only a fraction of the coil diameter (e.g., within a few centimeters), and the axes of the coils are closely aligned.

[0005] In some IPT systems, resonant inductive coupling is used. Resonant inductive coupling can improve the efficiency of IPT by using a resonant circuit. Resonant inductive coupling can achieve higher efficiency at longer distances than non-resonant inductive coupling. In resonant inductive coupling, power is transferred by a magnetic field between two resonant circuits, one in the transmitter and the other in the receiver. The two circuits are tuned to resonate at the same resonant frequency.

[0006] In some IPT systems, magnetic fields can generate eddy currents in nearby metal. This can lead to significant temperature increases and fire hazards. Ferromagnetic plates can be used to provide shielding and improve inductive coupling, but can add cost to such systems.

[0007] Capacitive power transfer (CPT) uses an electric field to transfer power between two electrodes, such as metal plates. Typically, four metal plates are used in a CPT system to form a capacitive coupler. Two metal plates act as power transmitters, while the other two act as power receivers, resulting in at least two coupling capacitors to provide a power flow loop. The transmitter applies an AC voltage to the transmitting plate. The oscillating electric field induces an AC potential on the receiver plate, which causes AC power to flow in the load circuit. Resonance can also be used with capacitive coupling to extend the power transfer range.

[0008] In a CPT system, eddy currents can be reduced, and the plates used are low cost and reduce system cost. However, a problem with many systems is that high voltages can be forced on the plates. Such high voltages can generate strong electric fields, which result in significant field emissions to the surrounding area.

[0009] There are also problems associated with capacitive or inductive compensation networks in CPT and IPT systems. Currently, both CPT and IPT systems require minimal spacing between the receiver and transmitter. This typically requires large capacitors and inductors in the compensation network on both the primary and secondary sides. It is difficult to produce these large components, and their parasitic resistance can significantly reduce system efficiency. In addition, these compensation components do not directly participate in the power transfer process.

[0010] Wireless power transmitters and receivers with fewer components and / or reduced cost are still desired. Wireless power transmitters and receivers with reduced reliance on compensation networks are still desired. Wireless power transmitters and receivers with higher efficiency are still desired. Wireless power transmitters with more flexible requirements for alignment and spacing therebetween are still desired. There is still a need for power transmission systems capable of transferring power in both forward and reverse directions between a load and a power source, including between a DC source and an AC grid.

[0011] The field of power delivery for consumer products is becoming increasingly important. In the automotive field, the wiring harness has become an important and expensive subsystem of the vehicle. The market for automotive wiring harnesses is expected to exceed $77 billion within this decade. In an era of concern about gas mileage for internal combustion vehicles, carbon emissions of such vehicles, and range for electric vehicles, the cost, weight, and power delivery efficiency of such wiring harnesses have become major concerns in vehicle design. Given that materials and components account for 57% of the cost of manufacturing a car, the concerns are understandable.

[0012] While battery technology is steadily improving to provide batteries with higher energy density, consumer demand for more and more auxiliary user electronics and electric drive systems integrated into vehicles is also increasing. This places increasing demands on battery and vehicle weight, cost, and power transmission efficiency. In the 1990s, the automotive industry proposed higher voltage battery systems, partly due to the desire to reduce wiring harness weight.

[0013] There have been many efforts to reduce the amount of expensive copper used in wiring harnesses, and there is a move towards using cheaper aluminum. This trend is also driven by the desire to save about 40 pounds of weight in a typical car. This trend towards aluminum has its own problems, in part because the resistivity of aluminum is 1.58 times that of copper. Aluminum also has a phenomenon called creep, which causes connections to loosen. In addition, aluminum will also oxidize, so precautions must be taken with connections. Some solutions for wiring harnesses still require copper, and any connection between copper and aluminum will introduce problems with current potential.

[0014] Therefore, there is a clear need for an alternative approach for vehicle wiring harnesses that reduces expensive copper content, provides flexibility in voltage, avoids the problems typified by aluminum, and reduces weight.

[0015] At the same time, the efficiency of power transmission technology needs to be improved to keep pace with the rapid advancement of battery technology, which in turn is stimulated by developments in the electric vehicle field.

[0016] For example, these requirements are not limited to the automotive sector, but also apply to the sector of solar power transmission and, after certain modifications, also to other household consumer devices, such as computers and television displays. Power conditioning units that optimally extract power from power sources with varying voltages are widely used today, but they are usually subject to a limited degree of control facilities. This in turn prevents optimization of the power transmission efficiency.

[0017] The above examples of the related art and limitations related thereto are intended to be illustrative and not exclusive. Other limitations of the related art will become apparent to those skilled in the art after reading this specification and studying the accompanying drawings. Summary of the invention

[0018] In a first scheme, a dual-peak near-field resonant wireless power transmission system is proposed, wherein the dual-peak near-field resonant wireless power transmission system is configured to simultaneously perform capacitive power transmission and inductive power transmission according to an adjustable transmission mode ratio at a resonant power signal oscillation frequency, the system comprising: a transmitter subsystem, including a transmitter antenna subsystem and a power signal tuner module, the tuner module being configured to adjust the transmission mode ratio by adjusting the power signal provided by the tuner module to the transmitter antenna subsystem; and a receiver subsystem, including a receiver antenna subsystem, the receiver antenna subsystem being configured to receive power from the transmitter antenna subsystem according to the transmission mode ratio.

[0019] The tuner module may be configured to adjust the power signal by adjusting the phase difference between the current and the voltage of the power signal provided to the transmitter antenna subsystem. The transmitter subsystem may further include: a controller; and at least one sensor, wherein the controller is configured to receive sensor information from the at least one sensor and to automatically provide a tuning instruction to the tuner module based on the sensor information; and the tuner module is configured to adjust the phase difference between the current and the voltage of the power signal provided to the transmitter antenna subsystem according to the tuning instruction.

[0020] The at least one sensor may be disposed on the transmitter subsystem. In other embodiments, the at least one sensor may be disposed on the receiver subsystem, and the controller may be configured to wirelessly receive the sensor information. The at least one sensor may be one of: a power load sensor, a transmit power sensor, a surrounding object detector, and a distance detector configured to monitor the distance between the transmitter antenna and the receiver antenna.

[0021] The resonant power signal oscillation frequency can be freely varied within a predetermined frequency band. The predetermined frequency band can be an Industrial, Scientific and Medical (ISM) band. The system can be detuned to a degree that allows the resonant power signal oscillation frequency to vary within opposite limits of the predetermined frequency band.

[0022] In yet another aspect, a wireless method for bimodally transmitting power according to an adjustable transmission mode ratio at a resonant power signal oscillation frequency is provided, the method comprising: providing a transmitter subsystem, the transmitter subsystem including a power signal tuner module and a transmitter antenna subsystem configured to resonate at the resonant power signal oscillation frequency; providing a receiver subsystem, the receiver subsystem including a receiver antenna subsystem configured to resonate at the resonant power signal oscillation frequency; providing a power signal from the tuner module to the transmitter antenna subsystem at the power signal oscillation resonant frequency; adjusting the transmission mode ratio by adjusting the power signal from the tuner module to the transmitter antenna subsystem; and receiving the transmitted power at the power signal oscillation resonant frequency via the receiver antenna subsystem in the receiver subsystem according to the transmission mode ratio. Adjusting the transmission mode ratio may include adjusting a phase difference between a current and a voltage of the power signal provided to the transmitter antenna subsystem.

[0023] Providing a transmitter subsystem may further include: providing a controller and at least one sensor, and the tuner module may adjust the phase difference between the current and the voltage through a command of the controller based on sensor information received by the controller from the at least one sensor. The controller may automatically send the command of the controller to the tuner module when receiving the sensor information; and the tuner module may automatically execute the command from the controller to change the phase difference.

[0024] The method may further include: allowing the resonant power signal oscillation frequency to vary within a predetermined frequency band. The predetermined frequency band may be an Industrial, Scientific and Medical (ISM) band. Providing a transmitter subsystem may include providing a transmitter subsystem that is detuned to an extent that allows the resonant power signal oscillation frequency to vary within opposite extremes of the predetermined frequency band.

[0025] In another embodiment, a dual-peak near-field resonant wireless power transmission system is provided, wherein the dual-peak near-field resonant wireless power transmission system is configured to simultaneously perform capacitive power transmission and inductive power transmission according to an adjustable transmission mode ratio of capacitive power transmission and inductive power transmission at a variable resonant power signal oscillation frequency, the system comprising: a transmitter subsystem, including a transmitter antenna subsystem and a power signal tuner module, wherein the power signal tuner module adjusts the transmission mode ratio by adjusting a power signal provided by the power signal tuner module to the transmitter antenna subsystem; and a receiver subsystem, including a receiver antenna subsystem, which receives power from the transmitter antenna according to the transmission mode ratio.

[0026] The system transmits information between the transmitter antenna subsystem and the receiver antenna subsystem via the transmitter antenna and the receiver antenna of the receiver antenna subsystem. The system may further include a modulator for modulating information onto an information-bearing signal and providing the information-bearing signal to the transmitter antenna subsystem. The system may modulate information onto an information-bearing signal and provide the information-bearing signal to the transmitter antenna subsystem. The modulator may be arranged to modulate the information-bearing signal to the transmitter antenna subsystem based on the information. The power signal tuner module may include the modulator.

[0027] The information bearing signal may have a frequency different from the variable resonant power signal oscillation frequency. The modulator may modulate the information bearing signal by any of frequency modulation, amplitude modulation, and phase modulation. The information bearing signal may be modulated so that the variable power signal oscillation frequency is a harmonic of the frequency of the information bearing signal. The information bearing signal may be modulated onto a harmonic of a power signal. The signal modulated and provided to the transmitter antenna subsystem may be the power signal.

[0028] The modulator may modulate a reflection characteristic of the receiver antenna and transmit the information from the receiver antenna subsystem to the transmitter antenna subsystem by modulating the reflection characteristic of the receiver antenna according to the information. The modulated reflection characteristic of the receiver antenna may be an impedance of the receiver antenna.

[0029] The system can transmit the information from the receiver subsystem to the transmitter subsystem by modulating the reflection of the signal from the transmitter subsystem by the receiver antenna. The receiver subsystem can modulate the reflection characteristics of the receiver antenna. The receiver subsystem can modulate the impedance of the receiver antenna.

[0030] An electrical load may be present at the output of the receiver subsystem; and the information may include one or more of the presence of the electrical load, a charging level of the electrical load, power transfer efficiency, a charging rate of the electrical load, a state of the electrical load, the presence of voltage across the electrical load, a charge capacity of the electrical load, and a remaining time to charge the electrical load.

[0031] The system may transmit digital information between the transmitter subsystem and the receiver subsystem via the transmitter antenna. The system may transmit analog information between the transmitter subsystem and the receiver subsystem via the transmitter antenna. The receiver subsystem may be configured to transmit power to a subsequent receiver subsystem. The receiver may further include a rectifier including a phase shifter.

[0032] In yet another aspect, a dual-peak resonant near-field radio frequency power transfer system is provided, comprising a plurality of power transmit-receive modules for simultaneously performing capacitive power transfer and inductive power transfer via a power signal according to an adjustable transfer mode ratio at a power signal frequency, wherein each of the plurality of power transmit-receive modules is in wired communication with a transmitter-receiver resonator, the transmitter-receiver resonator being configured to exchange power with at least another one of the plurality of power transmit-receive modules.

[0033] A first power transmit-receive module of the plurality of power transmit-receive modules may include a power signal tuner module, the power signal tuner module being adjustable for changing the transmit mode ratio by adjusting a power signal provided by the power signal tuner module to a transmitter-receiver resonator in wired communication with the first power transmit-receive module of the plurality of power transmit-receive modules. At least one of the plurality of power transmit-receive modules may include a modulator arranged to modulate information onto a radio frequency signal exchanged between an associated transmitter-receiver resonator in wired communication with at least one of the plurality of power transmit-receive modules and a transmitter-receiver resonator in wired communication with any other of the plurality of power transmit-receive modules.

[0034] The modulator may be any one of an amplitude modulator, a frequency modulator, and a phase modulator. The information may include one or both of digital information and analog information. The radio frequency signal modulated by the modulator may be a power signal. The radio frequency signal modulated by the modulator may have a frequency different from a power signal frequency. The radio frequency signal modulated by the modulator may have a frequency that is a harmonic of the power signal frequency. The power signal frequency may be a harmonic of the frequency of the modulated signal.

[0035] The modulator may be arranged to modulate a reflection characteristic of an associated wire-connected transmitter-receiver resonator in accordance with the information to impose the information on a signal reflected by the wire-connected transmitter-receiver resonator. The modulator may be arranged to modulate a signal provided to the associated transmitter-receiver resonator in accordance with the information. The power signal tuner module of the first of the plurality of power transmit-receive modules may include the modulator. Each of the power transmit-receive modules may include a compensation network, and the compensation network may include the modulator. At least one of the power transmit-receive modules may include a radio frequency oscillator that provides a signal to the at least one power transmit-receive module at the power signal frequency, and the radio frequency oscillator may include the modulator.

[0036] Each of the plurality of power transmit-receive modules may be reconfigured between a power transmitter mode and a power receiver mode. Each of the power transmit-receive modules may include a differential self-synchronous RF power amplifier / rectifier, which is capable of reconfiguring between an amplifier state and a rectifier state corresponding to the power transmitter mode and the power receiver mode of the power transmit-receive module, respectively. The differential self-synchronous RF power amplifier / rectifier may be a differential switching mode self-synchronous RF power amplifier / rectifier. Each of the power transmit-receive modules may include a controller, and the reconfiguration may be controlled by the controller. Each differential self-synchronous RF power amplifier / rectifier may include a phase shifter, which may be adjusted by the controller for reconfiguring the differential self-synchronous RF power amplifier / rectifier between the amplifier state and the rectifier state.

[0037] When a power load is present at the output of one of the multiple power transmit-receive modules in the receiver mode, the information may include one or more of the presence of the power load, the charging level of the power load, the power transfer efficiency, the charging rate of the power load, the state of the power load, the presence of voltage on the power load, the charge capacity of the power load, and the remaining time to charge the power load.

[0038] In yet another aspect, a near-field radio frequency method for transferring power via a power signal at a power signal frequency is provided, the method comprising: providing a dual-peak resonant near-field radio frequency power transfer system comprising a plurality of power transmit-receive modules, wherein each of the plurality of power transmit-receive modules is in wired communication with a transmitter-receiver resonator, the transmitter-receiver resonator being configured to exchange power with at least another of the plurality of power transmit-receive modules; and operating the power transfer system according to an adjustable transfer mode ratio for simultaneous capacitive power transfer and inductive power transfer.

[0039] A first power transmit-receive module among the plurality of power transmit-receive modules provided may include a power signal tuner module; and operating the power transfer system may include changing the transfer mode ratio by adjusting the power signal tuner module. Providing the power transfer system may include providing at least one power transmit-receive module among the plurality of power transmit-receive modules that is in wired communication with an associated transmitter-receiver resonator and has a modulator, and operating the power transfer system may include exchanging radio frequency signals between the associated transmitter-receiver resonator and a transmitter-receiver resonator in wired communication with at least another of the plurality of power transmit-receive modules; and modulating information onto the exchanged radio frequency signals. When a power load is present at the output of one of the plurality of power transmit-receive modules, the information may include, for example, without limitation, one or more of the presence of the power load, the charge level of the power load, the power transfer efficiency, the charging rate of the power load, the state of the power load, the presence of voltage on the power load, the charge capacity of the power load, and the remaining time to charge the power load.

[0040] The information may be modulated onto the exchanged radio frequency signal by amplitude modulation, frequency modulation or phase modulation. Modulating the information onto the exchanged radio frequency signal may include modulating digital information or analog information onto the exchanged radio frequency signal.

[0041] Modulating the information onto the exchanged radio frequency signal may include modulating the information onto the power signal. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having a frequency different from the power signal frequency. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having a frequency that is a harmonic of the power signal frequency. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having the power signal frequency as a harmonic.

[0042] Modulating the information onto the exchanged radio frequency signals may include modulating a reflection characteristic of the associated wire-connected transmitter-receiver resonator according to the information to impose the information on a signal reflected by the wire-connected transmitter-receiver resonator. Modulating the information onto the exchanged radio frequency signals may include modulating a signal provided to the associated transmitter-receiver resonator according to the information.

[0043] The method may include operating the power signal tuner module of the first power transmit-receive module of the plurality of power transmit-receive modules to modulate the information onto the exchanged RF signal. Each of the provided power transmit-receive modules may include a compensation network, and the compensation network may include the modulator, allowing the compensation network to be operated to modulate the information onto the exchanged RF signal. At least one of the power transmit-receive modules may include a RF oscillator that provides a signal to the at least one power transmit-receive module at the power signal frequency, and the RF oscillator may include the modulator, allowing the information to be modulated in the oscillator onto the exchanged RF signal.

[0044] Each of the multiple power transmit-receive modules provided can be reconfigured between a power transmitter mode and a power receiver mode; and the method can further include reconfiguring at least two of the multiple power transmit-receive modules between the power transmitter mode and the power receiver mode to reverse the power transmission direction between the at least two transmit-receive modules. Each of the power transmit-receive modules provided can include a differential self-synchronous RF power amplifier / rectifier that can be reconfigured between an amplifier state and a rectifier state corresponding to the power transmitter mode and the power receiver mode of the power transmit-receive module, respectively; and the method can include reconfiguring the differential self-synchronous RF power amplifier / rectifier of the at least two transmit-receive modules between the amplifier state and the rectifier state. Each differential self-synchronous RF power amplifier / rectifier may include a phase shifter that is adjustable for reconfiguring the differential self-synchronous RF power amplifier / rectifier between the amplifier state and the rectifier state; and the method may include adjusting the phase shifter of each of the differential self-synchronous RF power amplifier / rectifiers in the at least two transmit-receive modules.

[0045] In yet another aspect, a near-field resonant wireless power transfer system is provided, comprising: a transmit subsystem including a plurality of substantially mutually decoupled transmitter resonators, and a corresponding transmitter module in power signal communication with each transmitter resonator, each transmitter module including a transmit controller and a power signal source having a power signal oscillation frequency and a power signal phase, each power signal source being controlled by a corresponding transmit controller; one or more receiver subsystems, each including a corresponding receiver resonator; a software lookup table having discrete allowed power signal oscillation frequencies for the power signal source; and software, the software when loaded into memory and executed by a controller of any of the transmitter modules, performs the following actions: measuring one of an input impedance of the corresponding transmitter resonator and a test signal power draw of the corresponding transmitter resonator; and selecting a frequency for the corresponding power signal source from the lookup table based on one of the input impedance of the corresponding transmitter resonator and the test signal power draw of the corresponding transmitter resonator. The software when executed may perform the following actions: measuring a power level transmitted by the corresponding transmitter resonator while adjusting a phase of a power signal from the corresponding power signal source. The transmitter resonators may be substantially decoupled from each other by a grounded shielding mesh.

[0046] In yet another aspect, a wireless near-field method for transferring power from a multi-transmitter subsystem to a single resonant receiver subsystem at a variable resonant power signal oscillation frequency is provided, the method comprising: providing the multi-transmitter subsystem comprising a plurality of mutually independent transmitter resonators, each of the transmitter resonators being driven by a corresponding transmitter module, the corresponding electrically connected transmitter modules being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, wherein all of the transmitter resonators have a common emitting surface; arranging a resonant receiver subsystem proximate to the common emitting surface, the resonant receiver subsystem comprising a plurality of mutually independent transmitter resonators, each of the transmitter resonators being driven by a corresponding transmitter module, the corresponding electrically connected transmitter modules being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, wherein all of the transmitter resonators have a common emitting surface; and disposing a resonant receiver subsystem proximate to the common emitting surface, the resonant receiver subsystem comprising a plurality of mutually independent transmitter resonators, each of the transmitter resonators being driven by a corresponding transmitter module, the corresponding electrically connected transmitter modules being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band. The method further comprises: providing a plurality of independent transmitter resonators with a plurality of independent transmitter resonators, wherein the plurality of independent transmitter resonators are provided ...

[0047] In another embodiment, a wireless near-field method for transmitting power from a multi-transmitter subsystem to two or more receiver subsystems at a variable resonant power signal oscillation frequency is provided, the method comprising: providing the multi-transmitter subsystem comprising a plurality of mutually independent transmitter resonators, each of the transmitter resonators being driven by a corresponding transmitter module, the corresponding transmitter module being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, wherein all the transmitter resonators have a common transmitting surface; arranging the two or more resonant receiver subsystems close to the common transmitting surface, each resonant receiver subsystem comprising two or both of the transmitter resonators; The method further comprises: providing a single receiver resonator overlapped with the active transmitter resonator; measuring one of an input impedance of each of the transmitter resonators and a power drawn by each of the transmitter resonators from a test signal; setting a power signal to each of the plurality of mutually independent transmitter resonators to one of an off state and an active state based on the corresponding measured resonator input impedance and one of the power drawn by the corresponding transmitter resonator from the test signal; selecting a power signal oscillation frequency for each active transmitter resonator from the plurality of preset power oscillation frequencies based on the measured input impedance of the active transmitter resonator; and setting the power signal of each active transmitter resonator to the corresponding selected frequency. The method may further include adjusting a phase of the power signal applied to each corresponding transmitter resonator to a phase at which power transfer through the transmitter resonator is substantially maximum.

[0048] In yet another embodiment, a near-field wireless system for transmitting power from a photovoltaic cell to an electrical load is provided, the system comprising: a transmitting module in wired electrical communication with the photovoltaic cell, the transmitting module being configured to convert the power from the photovoltaic cell into an oscillating power signal having an oscillation frequency; a transmitter resonator in wired electrical communication with the transmitting module and being configured to resonate at the oscillation frequency; a receiver resonator configured to resonate at the oscillation frequency and arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; and a receiver module in wired electrical communication with the receiver resonator, the receiver module being configured to receive power from the receiver resonator and provide the received power to the electrical load in the form of direct current via wired electrical communication.

[0049] The transmit module may include a power amplifier configured to modulate the power received from the photovoltaic cell at the oscillation frequency. The transmit module may include an oscillator configured to provide the oscillation frequency to the power amplifier. The transmit module may include a controller and one or more sensors, the controller configured to change the oscillation frequency based on first information from at least one of the one or more sensors. The transmit module may include a transmission tuning network configured to change at least the phase of the power provided by the transmit module to the transmitter resonator based on second information from at least one of the one or more sensors under the control of the controller.

[0050] The system may include a power conditioning unit electrically connected between the photovoltaic cell and the transmitting module and configured to adapt power from the photovoltaic cell to a format compatible with the transmitting module. The transmitting module may include small signal electronic circuitry, and the power conditioning unit may be further configured to provide power to the small signal electronic circuitry. The transmitter resonator may be disposed on a surface of the photovoltaic cell opposite to an active solar radiation receiving surface of the cell. The transmitter resonator has a surface area having an extension that is at least a major portion of the extension of the active solar radiation receiving surface of the cell.

[0051] The transmitter resonator may have a planar area that is smaller than a planar area of ​​the receiver resonator.The receiver resonator may be arranged and configured to receive power from other transmitter resonators via at least one of capacitive coupling and magnetic induction at the resonant frequency.

[0052] In yet another embodiment of a near-field wireless system for transmitting power from an array of photovoltaic cells to an electrical load, the system includes: a first plurality of transmitter modules, each transmitter module being in wired electrical communication with a corresponding photovoltaic cell in the array, each transmitter module being configured to convert the power from the corresponding photovoltaic cell into an oscillating power signal having an oscillation frequency; a second plurality of transmitter resonators, each transmitter resonator being in wired electrical communication with a corresponding transmitter module from the first plurality of transmitter modules and being configured to resonate at the oscillation frequency; a single receiver resonator being configured to resonate at the oscillation frequency and being arranged to receive power from the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a receiver module being in wired electrical communication with the receiver resonator, the receiver module being configured to receive power from the receiver resonator and to provide the received power to the electrical load in the form of direct current via wired electrical communication.

[0053] Each transmit module from the first plurality of transmit modules may include a power amplifier configured to modulate power received from a corresponding photovoltaic cell at the oscillation frequency. Each transmit module from the first plurality of transmit modules may include an oscillator configured to provide the oscillation frequency to the corresponding power amplifier. Each transmit module from the first plurality of transmit modules may further include a controller and one or more sensors, the controller configured to vary the oscillation frequency based on first information from at least one of the one or more sensors. Each transmit module from the first plurality of transmit modules may include a transmission tuning network configured to at least change the phase of power provided by the transmit module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors under the control of the corresponding controller.

[0054] The system may include a third plurality of power conditioning units, each power conditioning unit from the third plurality of power conditioning units being electrically connected between a corresponding photovoltaic cell and a corresponding transmitter module and configured to adapt power from the corresponding photovoltaic cell to a format compatible with the corresponding transmitter module. Each transmitter module from the first plurality of transmitter modules may include small signal electronic circuitry, and the corresponding power conditioning unit may be further configured to provide power to the small signal electronic circuitry. Each transmitter resonator from the second plurality of transmitter resonators may be disposed on a surface of the corresponding photovoltaic cell opposite an active solar radiation receiving surface of the cell.

[0055] In yet another embodiment of a near-field wireless system for transferring power from an array of photovoltaic cells to an electrical load, the system includes: a first plurality of transmitter modules, each transmitter module being in wired electrical communication with a corresponding photovoltaic cell in the array, each transmitter module being configured to convert the power from the corresponding photovoltaic cell into an oscillating power signal having an oscillation frequency; a second plurality of transmitter resonators, each transmitter resonator being in wired electrical communication with a corresponding transmitter module from the first plurality of transmitter modules and configured to resonate at the oscillation frequency; a third plurality of receiver resonators being configured to resonate at the oscillation frequency, each receiver resonator from the third plurality of receiver resonators being configured to receive power from a corresponding transmitter resonator from the second plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a fourth plurality of receiver modules, each receiver module being in wired electrical communication with a corresponding receiver resonator from the third plurality of receiver resonators, the receiver modules being configured to receive power from the corresponding receiver resonator and to provide the received power to the electrical load in the form of direct current via wired electrical communication.

[0056] Each transmit module from the first plurality of transmit modules may include a power amplifier configured to modulate power received from a corresponding photovoltaic cell at the oscillation frequency. Each transmit module from the first plurality of transmit modules may include an oscillator configured to provide the oscillation frequency to the corresponding power amplifier. Each transmit module from the first plurality of transmit modules may further include a controller and one or more sensors, the controller configured to vary the oscillation frequency based on first information from at least one of the one or more sensors. Each transmit module from the first plurality of transmit modules may include a transmission tuning network configured to at least change the phase of power provided by the transmit module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors under the control of the corresponding controller.

[0057] The system may further include a fifth plurality of power conditioning units, each power conditioning unit from the fifth plurality of power conditioning units being electrically connected between a corresponding photovoltaic cell from the solar cell array and a corresponding transmitting module from the first plurality of transmitting modules, and configured to adapt power from the corresponding photovoltaic cell to a format compatible with the corresponding transmitting module. Each transmitting module from the first plurality of transmitting modules may include a small signal electronic circuit, and the corresponding power conditioning unit from the fifth plurality of power conditioning units may be further configured to provide power to the small signal electronic circuit. Each transmitter resonator from the second plurality of transmitter resonators may be disposed on a surface of a corresponding photovoltaic cell from the photovoltaic cell array opposite to an active solar radiation receiving surface of the cell.

[0058] In yet another embodiment, a near-field wireless system for transferring power from an array of photovoltaic cells to an electrical load is provided, the system comprising: a first plurality of transmitter modules, each transmitter module being in wired electrical communication with a corresponding photovoltaic cell in the array, each transmitter module being configured to convert power from the corresponding photovoltaic cell into an oscillating power signal having an oscillation frequency; a second plurality of transmitter resonators, each transmitter resonator being in wired electrical communication with a corresponding transmitter module from the first plurality of transmitter modules and being configured to resonate at the oscillation frequency; a third plurality of receiver resonators, which are less in number than the plurality of transmitter resonators and are configured to resonate at the oscillation frequency, each receiver resonator from the third plurality of receiver resonators being configured to receive power from a portion of the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; and a fourth plurality of receiver modules, each receiver module being in wired electrical communication with a corresponding receiver resonator, the receiver modules being configured to receive power from the corresponding receiver resonator and to provide the received power to the electrical load in the form of direct current via wired electrical communication.

[0059] Each transmit module from the first plurality of transmit modules may include a power amplifier configured to modulate power received from a corresponding photovoltaic cell at the oscillation frequency. Each transmit module from the first plurality of transmit modules may include an oscillator configured to provide the oscillation frequency to the corresponding power amplifier. Each transmit module from the first plurality of transmit modules may further include a controller and one or more sensors, the controller configured to vary the oscillation frequency based on first information from at least one of the one or more sensors. Each transmit module from the first plurality of transmit modules may include a transmission tuning network configured to at least change the phase of power provided by the transmit module to the corresponding transmitter resonator based on second information from at least one of the one or more sensors under the control of the corresponding controller.

[0060] The system may include a fifth plurality of power conditioning units, each power conditioning unit from the fifth plurality of power conditioning units being electrically connected between a corresponding photovoltaic cell from the photovoltaic cell array and a corresponding transmitting module from the first plurality of transmitting modules, and being configured to adapt power from the corresponding photovoltaic cell into a format compatible with the corresponding transmitting module.

[0061] Each transmitter module from the first plurality of transmitter modules may include small signal electronic circuitry, and a corresponding power conditioning unit from the fifth plurality of power conditioning units may be further configured to provide power to the small signal electronic circuitry. Each transmitter resonator from the second plurality of transmitter resonators may be disposed on a surface of a corresponding photovoltaic cell from the photovoltaic cell array opposite an active solar radiation receiving surface of the cell.

[0062] In yet another embodiment, a method for transmitting power from a photovoltaic cell to an electrical load is provided, the method comprising: converting power from the photovoltaic cell into an oscillating power signal having an oscillation frequency in a transmitting module; transmitting the power to a transmitter resonator that is in wired electrical communication with the transmitting module and configured to resonate at the oscillation frequency; receiving the power in a receiver resonator that is configured to resonate at the oscillation frequency and is arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; receiving the power in a receiver module that is in wired electrical communication with the receiver resonator; and providing the received power to the electrical load in the form of direct current via wired electrical communication.

[0063] In yet another embodiment of a method for transmitting power from an array of photovoltaic cells to an electrical load, the method includes: converting power from each of the photovoltaic cells in the array into an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmitting modules; transmitting power to a corresponding transmitter resonator from a second plurality of transmitter resonators in each of the transmitting modules, the transmitter resonators each being configured to resonate at the oscillation frequency; receiving power in a receiver resonator, the receiver resonator being configured to resonate at the oscillation frequency and being arranged to receive power from the plurality of transmitter resonators via at least one of capacitive coupling and magnetic induction; receiving power in a receiver module in wired electrical communication with the receiver resonator; and providing the received power in the form of direct current to the electrical load via wired electrical communication.

[0064] In yet another embodiment of a method for transmitting power from an array of photovoltaic cells to an electrical load, the method includes: converting power from each of the photovoltaic cells in the array into an oscillating power signal having an oscillating frequency in each of a first plurality of corresponding transmitting modules; transmitting power from each of the transmitting modules to a corresponding transmitter resonator from a second plurality of transmitter resonators, wherein each transmitter resonator is configured to resonate at the oscillation frequency; receiving power from each transmitter resonator in a corresponding receiver resonator configured to resonate at the oscillation frequency, wherein each receiver resonator is further configured and arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; receiving power from each receiver resonator in a corresponding receiver module in wired electrical communication with the receiver resonator; and providing the received power to the electrical load in the form of direct current via wired electrical communication.

[0065] In yet another embodiment of a method for transmitting power from an array of photovoltaic cells to an electrical load, the method includes: converting power from each of the photovoltaic cells of the array into an oscillating power signal having an oscillating frequency in each of a first plurality of corresponding transmitting modules; transmitting power from each of the transmitting modules to a transmitter resonator from a second plurality of transmitter resonators, wherein each transmitter resonator is configured to resonate at the oscillating frequency; receiving power from each transmitter resonator in any proximate receiver resonator in a third plurality of receiver resonators, the receiver resonator being configured to resonate at the oscillating frequency, wherein each receiver resonator is further configured and arranged to receive power from the transmitter resonator via at least one of capacitive coupling and magnetic induction; sharing the received power between the third plurality of receiver resonators; and providing the received power in the form of direct current to the electrical load via wired electrical communication, the received power coming from one or more of the third plurality of receiver resonators via the corresponding one or more receiver modules. The method may further include converting the voltage and current of the power from each photovoltaic cell into a voltage and current suitable for the corresponding transmitting module before converting the power into the oscillating power signal.

[0066] A power transmission system for supplying power from a DC power source to an electrical load is provided, the system comprising: a radio frequency power amplifier in wired electrical communication with the power source and configured to convert a DC voltage from the power source into an AC voltage signal having an oscillating frequency; an adjustable phase radio frequency rectifier in wired electrical contact with the electrical load and in radio frequency communication with the power amplifier, the rectifier configured to receive power transmitted from the amplifier; and a receiver controller in communication with the rectifier, the receiver controller configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting the current-voltage phase characteristic of the rectifier. The rectifier may be a differential self-synchronous radio frequency rectifier.

[0067] The receiver controller may be configured to automatically adjust the current-voltage phase characteristic of the rectifier. The power transmission system may further include a load management system that is in wired communication with the load and is disposed between the load and the rectifier in a power signal manner, the load management system being configured to increase the efficiency of power transmission by adjusting the input impedance of the rectifier. The load management system may be configured to automatically adjust the current-voltage phase characteristic of the rectifier.

[0068] The power transfer system may further include a transmitter controller in communication with the amplifier, the transmitter controller configured to increase the efficiency of power transfer by adjusting the current-voltage phase characteristic of the amplifier. The transmitter controller may be configured to automatically adjust the current-voltage phase characteristic of the amplifier to increase the efficiency of power transfer.

[0069] The power transfer system may further include an oscillator in communication with the amplifier and the transmitter controller. The transmitter controller may be configured to adjust an oscillation frequency via the oscillator.

[0070] The power amplifier may be in direct wired RF communication with the adjustable phase RF rectifier. The power amplifier may be in wireless near-field RF communication with the adjustable phase RF rectifier. The power transfer system may include: a transmitter resonator in wired RF communication with the power amplifier; and a receiver resonator in wired RF communication with the rectifier. The transmitter resonator and the receiver resonator may be in wireless near-field RF communication with each other. The power amplifier may be in at least one of capacitive near-field wireless RF communication and inductive near-field wireless RF communication with the rectifier. The power amplifier may be in bimodal near-field wireless RF communication with the rectifier.

[0071] The DC power source may include a rechargeable battery and the load may include an electric motor. The load may include a computer monitor. The resonant structure of the system may include at least one electrically conductive mechanical load that carries a structural component of the system.

[0072] The system may further include a power conditioning unit electrically disposed between the power source and the power transfer system, the power conditioning unit configured to adjust at least one of a current and a voltage from the power source to improve efficiency of power transfer.

[0073] Further provided is a method for transmitting power from a DC power source to an electrical load, the method comprising: providing a power transmission system in wired electrical communication with the power source, the power transmission system comprising an RF power amplifier in RF communication with an adjustable phase RF rectifier, the adjustable phase RF rectifier being in wired electrical contact with the electrical load; converting the power from the DC power source into an RF oscillating power signal in the amplifier; converting the RF oscillating power signal into a DC power signal in the rectifier; and adjusting the efficiency of the power transmission by adjusting the current-voltage phase characteristic of the rectifier. Providing the adjustable phase RF rectifier may include providing a differential self-synchronous RF rectifier.

[0074] The method may further include adjusting the efficiency of power transmission by adjusting the DC equivalent input resistance of the amplifier. Providing the power transmission system may include providing a load management system in wired communication between the rectifier and the load. Adjusting the DC equivalent input resistance of the amplifier may include adjusting the input impedance of the rectifier by adjusting the load management system. Adjusting the load management system may include automatically adjusting the load management system.

[0075] The method may further include adjusting the efficiency of the power transfer by adjusting a current-voltage phase characteristic of a power amplifier. Providing the power transfer system may include providing a transmitter controller in communication with the power amplifier to control the power amplifier. The adjusting the current-voltage phase characteristic of the power amplifier may be performed by the transmitter controller. The adjusting the current-voltage phase characteristic of the power amplifier may be performed automatically by the transmitter controller.

[0076] The method may further include adjusting the efficiency of power transfer by changing an oscillation frequency of the power amplifier.

[0077] Providing a power transmission system may include providing a receiver controller in communication with the rectifier to control the rectifier. The adjusting the current-voltage phase characteristic of the rectifier may be performed by the receiver controller. The adjusting the current-voltage phase characteristic of the rectifier may be performed automatically by the receiver controller.

[0078] Providing the power transfer system may include providing the power amplifier in direct wired radio frequency communication with an adjustable phase radio frequency rectifier. Providing the power transfer system may include providing the power amplifier in wireless near field radio frequency communication with the adjustable phase radio frequency rectifier.

[0079] Providing the power transfer system may include: a transmitter resonator that provides for wired radio frequency communication with the power amplifier; and a receiver resonator that provides for wired radio frequency communication with the radio frequency rectifier. The method may further include operating the transmitter resonator and the receiver resonator in wireless near-field radio frequency communication with each other. Providing the power transfer system may include providing the power amplifier in at least one of capacitive near-field wireless radio frequency communication and inductive near-field wireless radio frequency communication with the rectifier. Providing the power transfer system may include providing the power amplifier in bimodal wireless near-field communication with the rectifier and a receiver resonator.

[0080] The method may further include providing a power conditioning unit electrically disposed between a power source and a power transfer system; and adjusting the power conditioning unit to adjust at least one of a current and a voltage from the power source to improve efficiency of power transfer.

[0081] A method for transmitting power from a DC power source to an electrical load is further provided, the method comprising: providing a power transmission system that performs wired electrical communication with the power source, the power transmission system comprising: an oscillator that is capable of oscillating at an oscillation frequency; a power amplifier and a transmitter tuning network, both of which are under the control of a transmitter controller; and a receiver tuning network and a load management system, both of which are under the control of a receiver controller, the load management system performing wired electrical communication with the electrical load; converting the power from the power source into an oscillating power signal having an oscillation frequency in the power amplifier; transmitting the power signal from the power amplifier to the load management system via the transmitter tuning network and the receiver tuning network under the control of the transmitter controller; adjusting at least one of the oscillation frequency, the input DC equivalent resistance of the power amplifier, the transmitter tuning network, the receiver tuning network and the load management system to change the rate of power transmission; and providing the power received by the load management system to the electrical load in the form of DC power via wired electrical communication.

[0082] Transmitting the power signal via the transmitter tuning network and the receiver tuning network may include transmitting power by wired communication. Transmitting the power signal via the transmitter tuning network and the receiver tuning network may include transmitting power by wireless communication. Transmitting power by wireless communication may include transmitting power by near-field wireless communication. Transmitting power by near-field wireless communication may include transmitting power by at least one of capacitive coupling and inductive coupling.

[0083] Transmitting power from a DC power source may include transmitting power from at least one solar cell. Transmitting power from a DC power source may include transmitting power from at least one solar cell. Transmitting power from a DC power source may include transmitting power from a power source having a varying voltage.

[0084] In another embodiment, an electric system includes: a mechanical load bearing structure having a conductive first portion; an electrical load; and a power transfer system including at least one radio frequency resonator configured for near-field wireless power transfer, wherein the resonator at least partially includes the conductive first portion. The electric system may further include a rechargeable battery, and the electrical load may include an electric motor. The electric system may be an electric vehicle and the mechanical load bearing structure may include a chassis of the vehicle. The electric system may be a display monitor, and the mechanical load bearing structure may be at least one of a frame and a base of the monitor.

[0085] The electric power system may further include a power supply. The power transmission system may include: an RF power amplifier in wired electrical communication with the power supply and configured to convert a DC voltage from the power supply into an AC voltage signal having an oscillating frequency; an adjustable phase RF rectifier in wired electrical contact with the power load and in RF communication with the power amplifier, the rectifier configured to receive power transmitted from the amplifier; and a receiver controller in communication with the rectifier, the receiver controller configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting the current-voltage phase characteristic of the rectifier.

[0086] In another embodiment, an apparatus comprises: a mechanical load bearing structure having a conductive first portion; a power source; an electrical load; and a power transmission system comprising: an RF power amplifier in wired electrical communication with the power source and configured to convert a DC voltage from the power source into an AC voltage signal having an oscillating frequency; an adjustable phase RF rectifier in wired electrical connection with the electrical load and in RF communication with the power amplifier, the rectifier being configured to receive power transmitted from the amplifier; and a receiver controller in communication with the rectifier, the receiver controller being configured to adjust the efficiency of power transmission from the amplifier to the rectifier by adjusting a current-voltage phase characteristic of the rectifier; wherein the conductive first portion is configured to carry at least one of an RF signal from the amplifier and an RF signal to the rectifier.

[0087] The device may further include a load management system in wired communication with the load and disposed between the load and the rectifier in a power signal manner, the load management system being configured to increase the efficiency of power transmission by adjusting the input impedance of the rectifier. The device may further include a transmitter controller in communication with the amplifier, the transmitter controller being configured to increase the efficiency of power transmission by adjusting the current-voltage phase characteristic of the amplifier. The device may further include an oscillator in communication with the amplifier and the transmitter controller, wherein the transmitter controller is configured to adjust the oscillation frequency via the oscillator.

[0088] The power amplifier may be in direct wired RF communication with the rectifier via the conductive first portion. The power amplifier may be in wireless near-field RF communication with the rectifier. The power transfer system may include: a transmitter resonator in wired RF communication with the power amplifier; and a receiver resonator in wired RF communication with the rectifier, and one of the transmitter resonator and the receiver resonator may include the conductive first portion. The transmitter resonator and the receiver resonator may be in wireless near-field RF communication with each other. The power amplifier may be in at least one of capacitive near-field wireless RF communication and inductive near-field wireless RF communication with the rectifier. The power amplifier may be in bimodal near-field wireless RF communication with the rectifier. The DC power source may include a rechargeable battery, and the load may include an electric motor.

[0089] In some embodiments, a sealed bidirectional power transmission circuit device includes a plurality of terminals, the plurality of terminals are configured to communicate electrically with a device outside the sealed device, the sealed device includes within the sealed interior: a multi-terminal power switching device having at least one DC terminal, at least one AC terminal, and at least one control terminal, the multi-terminal power switching device being adjustable between an amplification condition and a rectification condition, and arranged to: bidirectionally transmit DC voltage and DC current via at least one DC terminal; and bidirectionally transmit a radio frequency power signal having amplitude, frequency, and phase via at least one AC terminal; in wired data communication with a controller, a phase, frequency, and duty cycle adjustment circuit is wired in electrical communication with the power switching device via the at least one control terminal, and arranged to: establish a radio frequency oscillation signal having the frequency and phase of the radio frequency power signal at the at least one control terminal of the power switching device; and adjust the power switching device between the amplification condition and the rectification condition by adjusting the phase of the radio frequency oscillation signal under the instruction of the controller. In some embodiments, the controller may be disposed within the sealed interior of the sealed bidirectional power transmission circuit device. The plurality of terminals of the sealed power transfer circuit device may include terminals for data communication between the controller and devices outside the sealed interior.

[0090] The RF power signal may have a duty cycle, and the phase, frequency and duty cycle adjustment circuit may be further arranged to adjust the duty cycle of the RF power signal by adjusting the duty cycle of the RF oscillation signal. The phase, frequency and duty cycle adjustment circuit may include a RF oscillator for generating the RF oscillation signal under instructions from the controller.

[0091] The sealed power transmission circuit device may further include a tuning network for wired data communication with the controller inside the seal, the tuning network performs wired electrical communication with the power switching device via the at least one AC terminal, and the tuning network is arranged to adjust the RF power signal to a tuned RF power signal under instructions from the controller. The bidirectional power transmission circuit device may include a modulator configured to modulate information onto the RF power signal. The modulator includes the tuning network. The modulator may be configured to modulate the RF power signal using information provided by the controller. The tuning network may include a harmonic termination network circuit, which is arranged to suppress harmonics of the RF oscillation signal in the RF power signal. The harmonic termination network may include one or more inductors and one or more of a first harmonic terminal, a second harmonic terminal, and a third harmonic terminal. The sealed power transmission circuit device may further include an amplitude / frequency / phase detector in wired data communication with the controller inside the seal, the amplitude / frequency / phase detector is configured to be in wired electrical communication with the tuning network and arranged to determine the amplitude, frequency and phase of any radio frequency power signal transmitted between the tuning network and the AC load / source outside the sealed device. The tuning network may further include one or more of a compensation network, a matching network and a filter.

[0092] The phase, frequency and duty cycle adjustment circuit may be arranged to receive instructions from the controller based on measurement data transmitted to the controller by the amplitude / frequency / phase detector. The phase, frequency and duty cycle adjustment circuit may be configured to adjust the RF oscillation signal based on a feedback signal received directly from the amplitude / frequency / phase detector. The tuning network may include a voltage-current tuner for adjusting the phase difference between the voltage and current of the tuned RF power signal based on measurement data from the amplitude / frequency / phase detector when the power switching device is in the amplification condition.

[0093] The sealed power transmission circuit device may further include a power management circuit inside the seal that performs wired electrical communication between the power switching device and a DC power source / load outside the sealed device, and the power management circuit is arranged to match the impedance of the power switching device with the external DC power source / load, and adjust the DC power transmitted between the power switching device and the DC power source / load based on the feedback signal received directly from the amplitude / frequency / phase detector. In other embodiments, the sealed power transmission circuit device may further include a power management circuit inside the seal that performs wired data communication with the controller and performs wired electrical communication between the power switching device and a DC power source / load outside the sealed device, and the power management circuit is arranged to match the impedance of the power switching device with the external DC power source / load, and adjust the DC power transmitted between the power switching device and the DC power source / load based on the measurement data transmitted to the controller by the amplitude / frequency / phase detector.

[0094] The sealed power transmission circuit device may further include a voltage / current detector in wired data communication with the controller inside the seal, and the voltage / current detector is configured to determine the DC voltage and DC current transmitted between the power switching device and the power management circuit. The phase, frequency and duty cycle adjustment circuit can be configured to receive instructions from the controller based on measurement data transmitted to the controller by the voltage / current detector. In other embodiments, the phase, frequency and duty cycle adjustment circuit can be configured to adjust the RF oscillation signal based on a feedback signal received directly from the voltage / current detector.

[0095] The sealed power transmission circuit device may further include a memory inside the seal for wired data communication with the controller, the amplitude / frequency / phase detector and the voltage / current detector, wherein the memory is configured to receive and store measurement data from the two detectors and provide signal data from the two detectors to the controller.

[0096] The sealed power transmission circuit device may further include a power management circuit inside the seal for wired electrical communication between the power switching device and the AC power source / load outside the sealed device, the power management circuit being configured to match the amplitude, frequency and phase of the power switching device with the external AC power source / load, and to adjust the AC power transmitted between the power switching device and the AC power source / load based on a feedback signal received directly from the amplitude / frequency / phase detector.

[0097] The sealed power transmission circuit device may further include a power management circuit inside the seal that performs wired data communication with the controller and performs wired electrical communication between the power switching device and the AC power source / load outside the sealed device, and the power management circuit is arranged to match the amplitude, frequency and phase of the transmission power switching device with the external AC power source / load, and adjust the DC power transmitted between the power switching device and the AC power source / load based on the measurement data transmitted by the amplitude / frequency / phase detector to the controller.

[0098] The sealed power transmission circuit device may further include a voltage / current detector in the sealed interior for wired data communication with the controller, wherein the voltage / current detector is configured to determine the DC voltage and DC current transmitted between the power switching device and the power measurement circuit.

[0099] In some embodiments, the phase, frequency and duty cycle adjustment circuit is arranged to receive instructions from the controller based on measurement data transmitted to the controller by the voltage / current detector. In some embodiments, the phase, frequency and duty cycle adjustment circuit is arranged to adjust the RF oscillation signal based on a feedback signal received directly from the voltage / current detector.

[0100] The sealed power transmission circuit device may further include a memory inside the seal for wired data communication with the controller, the amplitude / frequency / phase detector and the voltage / current detector, wherein the memory is arranged to receive and store measurement data from the two detectors and provide signal data from the two detectors to the controller.

[0101] The sealed power transmission circuit device may further include at least one of a Bluetooth communication circuit, a WiFi communication circuit, a Zigbee communication circuit, and a cellular communication technology circuit in the sealed interior for transmitting information between the controller and a device outside the sealed power transmission circuit device. The communication circuit may perform bidirectional wired communication with at least one communication antenna, and the communication antenna is arranged to communicate with a device outside the sealed power transmission circuit device. The antenna for the communication circuit may be arranged in the sealed interior of the sealed device.

[0102] The bidirectional power transmission circuit device may include a modulator configured to modulate information onto at least one of the RF power signal and the DC voltage. The modulator may include the power switching device. The modulator may be configured to modulate at least one of the RF power signal and the DC voltage using information provided by the controller. The modulator may further include the phase, frequency and duty cycle adjustment circuit.

[0103] In some embodiments, all circuit elements of the bidirectional power transmission circuit device can be monolithically integrated in a silicon single crystal wafer. In some embodiments, at least a portion of the circuit elements of the device can be integrated by flip chip technology.

[0104] In one specific embodiment, the electronic circuit of the sealed bidirectional power transmission circuit device can be implemented in conjunction with at least one photovoltaic cell used as a DC source / load within a single silicon single crystal wafer. In another embodiment, the electronic circuit of the sealed bidirectional power transmission circuit device can be implemented in conjunction with at least one photovoltaic cell used as a DC source / load 700 within a single silicon single crystal wafer and a resonator structure used as an AC load / source on a surface of the silicon single crystal wafer. Antennas for Bluetooth, WiFi, Zigbee, and cellular technologies can also be integrated on the same single silicon single crystal wafer.

[0105] In another aspect, a power transfer system for transferring power between a DC source and a variable load is provided. A first self-synchronous RF rectifier / amplifier and a second self-synchronous RF rectifier / amplifier are configured to extract a first high frequency (HF) power signal and a second high frequency (HF) power signal from the DC source at a first high frequency frequency and a second high frequency frequency, respectively. A high frequency power link system is configured to receive and mix the first high frequency power signal and the second high frequency power signal to generate a transferred power signal. A power signal conversion circuit in communication with the high frequency power link system and the variable load is configured to generate an output power signal from the transferred power signal and supply the output power signal to the variable load.

[0106] The power transmission system further includes: a high-frequency switching signal generator configured to supply a first switching signal and a second switching signal to the first rectifier / amplifier and the second rectifier / amplifier at respective first high-frequency frequencies and second high-frequency frequencies, and to establish and control a mutual phase relationship between the first switching signal and the second switching signal.

[0107] The power signal conversion circuit includes: a switching mode rectifier, configured to receive the transmitted power signal from the high-frequency power link system and rectify the transmitted power signal to generate a rectified power signal; and an expansion circuit, configured to receive the rectified power signal from the switching mode rectifier and expand the rectified power signal to generate the output power signal.

[0108] The first self-synchronous RF rectifier / amplifier and the second self-synchronous RF rectifier / amplifier can be configured to operate in a rectification mode, and the switching mode rectifier can be configured to operate in a normally-on mode, thereby allowing power to be extracted from the variable load and transmitted to the DC source via the power signal conversion circuit and the high-frequency power link system.

[0109] The unfolding circuit can be configured to receive a reference signal from the variable load to unfold the rectified power signal synchronized with the signal in the variable load. The power signal conversion circuit, the high frequency power link system and the multiple pairs of self-synchronous radio frequency rectifiers / amplifiers can be configured to transmit control information from the rest of the system to the high frequency switching signal generator. The system can further include one or more controllers that communicate data with multiple elements of the system and are configured to control the multiple elements. The system can further include: an isolable load information circuit configured to transmit information about at least one of the DC level, frequency and phase of the power signal in the variable load to the high frequency switching signal generator. The load information circuit can include a phase-locked loop. The load information circuit can further include an isolator system, which can include an air gap. The high frequency power link system can include a wireless power link system, which can be a bimodal wireless high frequency power link system. The high frequency power link system can include a wired power link system.

[0110] In two phase difference based embodiments, the first high frequency frequency and the second high frequency frequency are the same frequency; and the first switching signal and the second switching signal may have a mutual phase difference that can be adjusted by the high frequency switching signal generator. In the first phase difference based embodiment, the high frequency switching signal generator is configured to adjust the mutual phase difference between the first switching signal and the second switching signal based on the DC level in the variable load, thereby generating the transmitted power signal from the high frequency power link system as a DC signal adjusted accordingly in amplitude. In the second phase difference based embodiment, the high frequency switching signal generator is configured to modulate the mutual phase difference between the first switching signal and the second switching signal at a phase modulation frequency derived from the frequency of the power signal in the variable load, thereby generating the transmitted power signal from the high frequency power link system as an AC power signal modulated at the frequency of the power signal in the variable load.

[0111] In a frequency difference based implementation, the first high frequency frequency and the second high frequency frequency differ by a difference frequency Δf. In this implementation, the high frequency switching signal generator is configured to determine the first high frequency frequency and the second high frequency frequency, and set the difference frequency Δf to double the frequency of the power signal in the variable load. The high frequency power link system is configured to generate the transmitted power signal at the difference frequency Δf, and the power signal conversion circuit is configured to supply the output power signal to the variable load at the frequency of the power signal in the variable load.

[0112] In another embodiment, a method for transmitting power between a DC source and a variable load is provided, the method comprising: extracting a corresponding first high frequency (HF) power signal and a second high frequency (HF) power signal from the DC source at a first high frequency frequency and a second high frequency frequency via a corresponding first self-synchronous RF rectifier / amplifier and a second self-synchronous RF rectifier / amplifier; receiving and mixing the first high frequency power signal and the second high frequency power signal in a high frequency power link system to generate a transmitted power signal; generating an output power signal from the transmitted power signal in a power signal conversion circuit that communicates with the high frequency power link system and the variable load; and supplying the output power signal to the variable load.

[0113] The method may further include: generating a first switching signal and a second switching signal in a high-frequency switching signal generator, and transmitting the first switching signal and the second switching signal to the first rectifier / amplifier and the second rectifier / amplifier at respective first high-frequency frequencies and second high-frequency frequencies; and establishing and controlling the mutual phase relationship between the first switching signal and the second switching signal in the high-frequency switching signal generator. The method may further include: receiving the transmitted power signal from the high-frequency power link system and rectifying the transmitted power signal in a switch-mode rectifier of the power signal conversion circuit; and receiving the rectified power signal from the switch-mode rectifier and expanding the rectified power signal in an expansion circuit of the power signal conversion circuit. The method may further include: setting the first self-synchronous RF rectifier / amplifier and the second self-synchronous RF rectifier / amplifier to a rectification mode; setting the switch-mode rectifier to a normally-on mode; extracting power from the variable load; and transmitting the extracted power to the DC source via the power signal conversion circuit and the high-frequency power link system.

[0114] The method may further include: developing the rectified power signal synchronized with the signal in the variable load based on a reference signal from the variable load; transmitting control information from the rest of the system to the high-frequency switching signal generator via the power signal conversion circuit, the high-frequency power link system, and the first self-synchronous RF rectifier / amplifier and the second self-synchronous RF rectifier / amplifier; controlling the multiple elements of the system through one or more controllers in data communication with the multiple elements; and transmitting information about at least one of the DC level, frequency, and phase of the power signal in the variable load to the high-frequency switching signal generator using an isolatable load information circuit including a phase-locked loop and an optional isolator system. Transmitting the power signal in the high-frequency power link system may include transmitting the power signal wirelessly, transmitting bimodally wirelessly, or transmitting the power signal wiredly.

[0115] Two methods for transmitting power from the DC source to the variable load employ a phase difference between switching signals. In such embodiments, the first switching signal and the second switching signal can have the same frequency and a mutual phase difference that can be adjusted by the high-frequency switching signal generator. The method for the first of such embodiments includes: adjusting the mutual phase difference between the first switching signal and the second switching signal based on the DC level in the variable load to generate the transmitted power signal from the high-frequency power link system as a DC signal that is correspondingly adjusted in amplitude. The method for the second of such embodiments includes: modulating the mutual phase difference between the first switching signal and the second switching signal at a phase modulation frequency derived from the frequency of the power signal in the variable load to generate the transmitted power signal from the high-frequency power link system as an AC power signal modulated at the frequency of the power signal in the variable load.

[0116] A method for an implementation based on a frequency difference includes: determining a first high frequency frequency and a second high frequency frequency of a corresponding first switching signal and a second switching signal; and setting the frequency difference equal to twice the frequency of a power signal in a variable load. The method further includes: generating a transmitted power signal from a high frequency power link system at the frequency difference; and supplying an output power signal to the variable load at the frequency of the power signal in the variable load.

[0117] The power transmission system described herein uses the phase difference or frequency difference between the switching signals supplied to a pair of self-synchronous radio frequency rectifier / amplifiers to transmit AC or DC power from a DC source to a variable load, which can be expanded to transmit power from a single DC source to a single variable load via multiple pairs of rectifier / amplifiers, and to transmit power from multiple DC sources to a single variable load using multiple pairs of rectifier / amplifiers. Apparatus and methods for achieving these purposes are described. In certain embodiments, these apparatus and methods also allow for simultaneous transmission of DC power and AC power to a load.

[0118] In one aspect, a system for transmitting power from at least one DC power source to a variable load is provided, the system comprising: a corresponding high-frequency power module disposed proximate to and in electrical communication with each of the at least one DC power source; and a single aggregator configured to receive power from the corresponding at least one DC power source via all at least one high-frequency power modules. Each of the at least one high-frequency power module may include a high-frequency switching signal generator and a pair of differential self-synchronous radio frequency rectifier / amplifiers, both of the rectifier / amplifiers in the pair being in wired electrical communication with the DC power source corresponding to the at least one high-frequency power module and configured to extract power from the corresponding DC power source. The high-frequency switching signal generator may be configured to provide a switching signal to the corresponding pair of differential self-synchronous radio frequency rectifier / amplifiers.

[0119] All the high frequency power modules can be phase locked to each other. The high frequency power modules can be phase locked to each other via a phase locked loop to an AC power signal in the variable load. The phase locked loop can be incorporated into the corresponding high frequency power module.

[0120] Each of the at least one high-frequency power module may include a high-frequency link in wired electrical communication with both differential self-synchronous RF rectifier / amplifiers to receive and mix power signals from the two differential self-synchronous RF rectifier / amplifiers and transmit a mixed power signal on a wired basis. Each of the at least one high-frequency power module may include a switch-mode rectifier in wired electrical communication with the high-frequency link, wherein the switch-mode rectifier is configured and arranged to receive the mixed power signal and rectify the mixed power signal, and transmit a rectified power signal on a wired basis. Each of the at least one high-frequency power module may include an expansion circuit configured and arranged to receive the rectified power signal from the switch-mode rectifier to expand the rectified power signal and transmit an expanded power signal on a wired basis.

[0121] The system may include a dual-peak wireless near-field high-frequency link system, wherein each of at least one high-frequency power module includes a primary side of the high-frequency link system in wired electrical communication with both a differential self-synchronous RF rectifier / amplifier in at least one high-frequency power module. The system may include a single collective secondary side of the high-frequency link system, configured to receive power from all at least one high-frequency link primary sides, and the secondary side may include a single receiver resonator and a single receiver module. The receiver module may be included in an aggregator along with a switch-mode rectifier and an unfolding circuit, wherein the switch-mode rectifier is in wired electrical communication with the receiver module and the unfolding circuit to receive a mixed power signal from the receiver resonator and rectify the mixed power signal, and the unfolding circuit is in wired electrical communication with a connection unit and configured to receive and unfold a rectified power signal from the rectifier and provide the rectified power signal to a variable load. The switching signals provided by the high-frequency switching signal generator to the two differential self-synchronous RF rectifiers / amplifiers may differ by one of a predetermined frequency difference and a predetermined phase difference. The system may include a controller, wherein the controller is configured to transmit at least one of a frequency and a phase determined by the controller to the high-frequency switching signal generator based on information about the load and about the DC source. The high-frequency power module may include the controller.

[0122] In some embodiments, the at least one DC source may be a photovoltaic cell and the system may include: a planar transparent solar cover having a planar first solar cover surface and a second solar cover surface; and a frame for mounting the transparent solar cover, wherein at least one photovoltaic cell is disposed on the first solar cover surface, and a planar photosensitive surface of at least one photovoltaic cell faces the first solar cover surface. Each high-frequency power module may include a high-frequency power circuit located on a printed circuit board, which is in wired electrical communication with the corresponding at least one photovoltaic cell. The high-frequency power circuit may be disposed on a planar surface of the printed circuit board facing away from the first solar cover surface.

[0123] The system may include a conformal encapsulation layer bonded to the first solar cover surface and covering at least one photovoltaic cell and a corresponding high frequency power module. The system may further include a dielectric protective cap located above the high frequency power circuit. The protective cap may be disposed above or below the conformal encapsulation layer. The periphery of the protective cap may be disposed below the conformal encapsulation layer and sealed to the conformal encapsulation layer, wherein the protective cap protrudes through the conformal encapsulation layer.

[0124] The printed circuit board may be disposed proximate to the corresponding at least one photovoltaic cell. In certain embodiments, the printed circuit board may be disposed on an insulating layer disposed on a rear surface of the photovoltaic cell. At least one photovoltaic cell may be configured in an array. The planar first solar cover surface may include an optically transparent polymeric layer.

[0125] A method for manufacturing a solar panel is provided, the method comprising: arranging at least one photovoltaic cell and a corresponding high-frequency power module on a planar surface of a transparent solar cover, the at least one photovoltaic cell having a photosensitive surface facing the planar surface of the transparent solar cover, the corresponding high-frequency power module comprising a high-frequency power circuit located on a printed circuit board, which performs wired communication with the at least one photovoltaic cell and is used to collect power from the at least one photovoltaic cell, wherein the high-frequency power circuit is arranged on a planar surface of the PC board facing away from the transparent solar cover; and disposing a heat-deformable polymer sheet on a side of the at least one photovoltaic cell opposite to the transparent solar cover, the heat-deformable polymer sheet The sheet extends over the surface area of ​​the transparent solar cover to form a laminated stack in a plane; transferring the laminated stack to a vacuum oven; establishing a vacuum in the vacuum oven to remove air between the layers of the laminated stack; heating the laminated stack to a deformation temperature of the heat-deformable polymeric sheet; applying mechanical pressure to the stack perpendicular to the plane; restoring an ambient air pressure in the vacuum oven to bond the heat-deformable polymeric sheet to the transparent solar cover and force the heat-deformable polymeric sheet to conformally bond to the at least one photovoltaic cell and the high-frequency power module to form a packaged photovoltaic module array; and mounting the packaged photovoltaic module array in a frame.

[0126] The method may further include disposing a transparent thermally cross-linkable polymer sheet on the transparent solar cover before disposing the at least one photovoltaic cell and the high frequency power module on the transparent solar cover.

[0127] Arranging the heat-deformable polymer sheet may include arranging a heat-deformable cross-linkable polymer sheet. Arranging the heat-deformable cross-linkable polymer sheet may include arranging a sheet comprising one or more layers of one or more of the following materials: polyethylene terephthalate, biaxially oriented polyethylene terephthalate, ethylene vinyl acetate, fluorinated polyester, polyvinyl fluoride, polyvinylidene fluoride, polyethylene vinyl acetate, polyethylene naphthalate, ethylene-tetrafluoroethylene, fluorovinyl ether, tetrafluoroethylene-hexafluoropropylene-vinylidene fluoride copolymer, polyamide, polypropylene, polyethylene, and polyvinylidene fluoride short sugar palm fiber. BRIEF DESCRIPTION OF THE DRAWINGS

[0128] Exemplary embodiments are illustrated in the referenced drawings. In the drawings, which are not necessarily drawn to scale, numbering may describe similar components in different views. Similar numbers with different letter suffixes may represent different instances of similar components. The drawings generally illustrate various embodiments discussed herein by way of example and not by way of limitation. The embodiments and drawings disclosed herein are to be considered illustrative and not restrictive.

[0129] Figure 1 is a schematic diagram of a wireless power transfer system according to an example embodiment.

[0130] Figure 2A , 2B 2C depict antennas that may be used in various example embodiments either alone or in combination with other disclosed elements.

[0131] Figure 3A and 3B Depicted is a side profile view of an antenna that may be used in various example embodiments either alone or in combination with other disclosed elements.

[0132] Figure 4A , 4B 4C and 4D depict side profile views of example resonators that may be used in various example embodiments either alone or in combination with other disclosed elements.

[0133] Figure 5 Depicted are cross sections of example resonators that may be used in various example embodiments either alone or in combination with other disclosed elements.

[0134] Figure 6 is a schematic illustration of the primary side of a wireless power transfer system according to an example embodiment.

[0135] Figure 7 is a schematic drawing of a secondary side of a wireless power transfer system according to an example embodiment.

[0136] Figure 8 is a schematic illustration of an exemplary power amplifier that may be used in various exemplary embodiments either alone or in combination with other disclosed elements.

[0137] Fig. 9 is a schematic drawing of an exemplary self-synchronous rectifier that may be used in various example embodiments either alone or in combination with other disclosed elements.

[0138] Fig.10 Shown according to an example Figure 6 A more detailed schematic diagram of a V / I tuner used to adjust the power signal to the transmitter resonator.

[0139] Fig.11 A flow chart is shown for a near field resonant wireless method for bimodally transmitting power according to an adjustable transmission mode ratio at a resonant power signal oscillation frequency according to an example embodiment.

[0140] Fig.12 is a schematic representation of a multi-transmitter near-field resonant wireless power transfer system for transferring power to a single receiver subsystem.

[0141] Fig.13A and 13B Depicted is a multi-transmitter near-field resonant wireless power transfer system for transferring power to a single receiver subsystem.

[0142] Fig.14 A multi-transmitter near-field resonant wireless power transfer system for transferring power to more than one receiver subsystem is depicted.

[0143] Fig.15 A flow chart is shown of a wireless near-field method for transferring power from multiple transmitter subsystems to a single resonant receiver subsystem at a variable resonant power signal oscillation frequency.

[0144] Fig.16 A flow chart illustrating another wireless near-field method for transferring power from multiple transmitter subsystems to a single resonant receiver subsystem at a variable resonant power signal oscillation frequency.

[0145] Fig.17 A flow chart is shown of a wireless near-field method for transferring power from a multiple transmitter subsystem to more than one resonant receiver subsystem at a variable resonant power signal oscillation frequency.

[0146] Fig.18 A flow chart is shown of another wireless near-field method for transferring power from a multiple transmitter subsystem to more than one resonant receiver subsystem at a variable resonant power signal oscillation frequency.

[0147] Fig.19A A near-field resonant wireless power transfer system for wirelessly transferring power from a photovoltaic solar cell to an electrical load is shown.

[0148] Fig.19B A power transfer system for transferring power from a photovoltaic solar cell to an electrical load is shown.

[0149] Fig. 20A and 20B Show configuration for use in a many-to-one configuration Fig.19A Front and rear views of a solar cell array of a near-field resonant wireless power transfer system.

[0150] Fig.21A and21B The configuration shown is for use in a one-to-one configuration Fig.19A Front and rear views of a solar cell array of a near-field resonant wireless power transfer system.

[0151] Fig.22A and 22B Shows the configuration for use in a row-based configuration Fig.19A Front and rear views of a solar cell array of a near-field resonant wireless power transfer system.

[0152] Fig.23 A diagram showing a flow chart of a method for wirelessly transferring power from a photovoltaic solar cell to an electrical load.

[0153] Fig.24 A flow chart illustrating another method for wirelessly transferring power from a photovoltaic solar array to an electrical load.

[0154] Fig.25 A flow chart illustrating another method for wirelessly transferring power from a photovoltaic solar array to an electrical load.

[0155] Fig.26 A flow chart illustrating another method for wirelessly transferring power from a photovoltaic solar array to an electrical load.

[0156] Fig.27A A diagram showing a portion of an electric vehicle utilizing an embodiment of a power transfer system.

[0157] Fig.27B Another diagram showing a portion of an electric vehicle utilizing an embodiment of the power transfer system.

[0158] Fig.28A Diagram showing a computer monitor using an embodiment of the power delivery system.

[0159] Fig.28B A computer monitor is shown using another embodiment of the power delivery system.

[0160] Fig.29 A flow chart illustrating a method for delivering power from a DC power source to an electrical load.

[0161] Fig.30 A flow chart illustrating yet another method for delivering power from a DC power source to an electrical load.

[0162] Fig.31 A flow chart illustrating a method for transferring power between transmit-receive modules in a dual-peak resonant near-field radio frequency power transfer system.

[0163] Fig.32A schematic diagram showing a bidirectional power transfer circuit arrangement.

[0164] Fig.33 An implementation of a bidirectional power transfer circuit arrangement is shown.

[0165] Fig.34A An embodiment of a bidirectional power transfer circuit device implemented in the same silicon wafer as a photovoltaic cell is shown.

[0166] Fig.34B Show Fig.34A Combined device with resonator on the surface of a silicon wafer.

[0167] Fig.35A A near-field resonant wireless power transfer system for wirelessly transferring power from a photovoltaic solar cell to an AC power load is shown.

[0168] Fig.35B A power transfer system for transferring power from a photovoltaic solar cell to an AC power load is shown.

[0169] Fig.36 A schematic diagram showing a bidirectional power transfer circuit arrangement.

[0170] Fig.37A A schematic diagram showing a bidirectional power transfer system for transferring power between a DC power source and an AC power load using a frequency difference of two high frequency signals.

[0171] Fig.37B A schematic diagram showing a bidirectional power transfer system for transferring power, which may be AC ​​or DC, between a DC power source and a variable power load using the phase difference of two high frequency signals.

[0172] Fig.37C A schematic diagram of a bidirectional power transfer system for transferring power, which may be AC ​​or DC, between a DC power source and a variable power load using a phase or frequency difference of two high frequency signals and multiple pairs of rectifiers / amplifiers is shown.

[0173] Fig.37D A schematic diagram of a bidirectional power transfer system for transferring power, which may be AC ​​or DC, between multiple DC power sources and variable power loads using a phase difference or frequency difference between two high frequency signals and multiple high frequency switching signal generators and multiple pairs of rectifiers / amplifiers is shown.

[0174] Fig.38 The results of the rectified power signal and the expanded power signal are shown in the form of a series of half waves.

[0175] Fig.39 A flow chart showing a method for transferring power, which may be AC ​​or DC, between a DC power source and a variable electrical load.

[0176] Fig.40 An exploded rear view of a photovoltaic module for wirelessly transmitting power including photovoltaic cells and a high-frequency power module is shown.

[0177] Fig.41A A power transfer system for wirelessly or wiredly transferring power, which may be AC ​​or DC, from photovoltaic cells in a solar panel having a plurality of photovoltaic cells to a variable power load is shown.

[0178] Fig.41B A bimodal wireless power transfer system for transferring power, which may be AC ​​or DC, from photovoltaic cells in a solar panel having multiple photovoltaic cells to a variable power load is shown.

[0179] Fig.42A is a schematic exploded rear view of a solar panel for wireless or wired transmission of power based on a photovoltaic module array prior to conformal application of an encapsulation layer.

[0180] Fig.42B is a schematic exploded rear view of a solar panel for bimodal wireless transmission of power based on a photovoltaic module array prior to conformal application of an encapsulation layer.

[0181] Fig.43A A schematic side view of a photovoltaic module encapsulated under a conformal encapsulation layer is shown.

[0182] Fig.43B A schematic side view of yet another embodiment of a photovoltaic module encapsulated under a conformal encapsulation layer is shown.

[0183] Fig.44 is a schematic exploded rear view of a solar panel for wirelessly transmitting power based on an array of photovoltaic modules including protective caps prior to conformal application of an encapsulation layer.

[0184] Fig.45 A flow chart showing a method for making a solar panel.

[0185] In all views, corresponding reference numerals indicate corresponding parts. Although the drawings represent embodiments of the invention, the drawings are not necessarily drawn to scale and certain features may be exaggerated in order to better illustrate and explain the invention. The flow charts are also representative in nature, and actual embodiments of the invention may include other features or steps not shown in the drawings. The examples set forth herein illustrate one embodiment of the invention in one form, and such examples should not be construed as limiting the scope of the invention in any way. DETAILED DESCRIPTION

[0186] In the following detailed description, specific details are set forth to provide a more thorough understanding to those skilled in the art. However, well-known elements may not be shown or described in detail to avoid unnecessarily obscuring the present invention. Therefore, this specification and the accompanying drawings should be viewed in an illustrative rather than a restrictive sense.

[0187] One embodiment of the present invention provides a wireless power transfer system including a transmitter (also referred to as a primary side) and a receiver (also referred to as a secondary side). Another scheme provides a wireless power transmitter that can be used as part of other wireless power transfer systems. Another scheme provides a wireless power receiver that can be used as part of other wireless power transfer systems. A transmitter according to certain embodiments may include a resonator configured to transmit power by inductive power transfer and / or by capacitive power transfer. Similarly, a receiver according to certain embodiments may include a resonator configured to receive power by inductive power transfer and / or by capacitive power transfer.

[0188] Figure 1 1 is a simplified schematic diagram of a wireless power transfer (WPT) system 10 including a primary side 12 and a secondary side 14. The primary side 12 may also be referred to as a transmitter, and the secondary side 14 may also be referred to as a receiver. The primary side 12 includes: a transmitter module 20; and a transmitter resonator 30, and the secondary side 14 includes: a receiver module 40; and a receiver resonator 50.

[0189] The transmitter module 20 receives power as input, including, for example, direct current (DC) power. Although not depicted, the transmitter module 20 may include, for example, an inverter, a transmitter compensation network, and / or other components as further described herein. The transmitter module 20 delivers power, including, for example, alternating current (AC) power, as output to the transmitter resonator 30.

[0190] The transmitter resonator 30 receives power as input from the transmitter module 20 and can output a magnetic field 31A (e.g., a time-varying magnetic field) and / or an electric field 31B (e.g., a time-varying electric field). In some embodiments, the transmitter resonator 30 outputs the magnetic field 31A for the purpose of IPT. In some embodiments, the transmitter resonator 30 outputs the electric field 31B for the purpose of CPT. In some embodiments, the resonator 30 outputs both the magnetic field 31A and the electric field 31B for the purpose of transmitting power through CPT and IPT simultaneously. In some embodiments, the resonator 30 can switch between outputting the electric field 31B for the purpose of CPT, outputting the magnetic field 31A for the purpose of IPT, and outputting both the magnetic field 31A and the electric field 31B for the purpose of transmitting power through CPT and IPT simultaneously.

[0191] The adjective term "bimodal" is used herein to describe a system configured for simultaneous capacitive signaling and inductive signaling.

[0192] In the presence of a magnetic field 31 A, for the purposes of IPT, a current may be induced in the receiver resonator 50. In the presence of an electric field 3 IB, an AC potential may be induced across the receiver resonator 50 (or its antenna or antennas).

[0193] When a current is induced in the receiver resonator 50 by the magnetic field 31A, the current may be output to the receiver module 40. Similarly, when an AC potential is induced on the receiver resonator 50 by the electric field 31B, a current may be caused to flow into the receiver module 40 by the receiver resonator 50.

[0194] The receiver module 40 may receive power (e.g., AC power) as input from the receiver resonator 50 and may output power (e.g., DC power) to a load. The load may be a charge for an electrical storage device such as a battery or supercapacitor. By way of non-limiting example, the load may include or be a component of an electric bicycle (also known as an e-bike or e-pedelec) such as an e-bike that is part of a shared bike fleet, an automobile, a boat, etc. Although not shown, the receiver module 40 may include, for example, a rectifier, a receiver compensation network, and / or other components as further discussed herein.

[0195] For various reasons, the WPT system 10 may be configured to adjust the ratio of power transmitted from the transmitter module 20 to the receiver module 40 via CPT to the power transmitted from the transmitter module 20 to the receiver module 40 via IPT ("transmission mode ratio"). For example, the transmission mode ratio may be adjusted to: increase the ratio of power delivered by CPT as the distance between the transmitter resonator 30 and the receiver resonator 50 increases; increase the ratio of power delivered by IPT when a living being (e.g., a human or animal) is near the WPT system 10; increase the ratio of power delivered by CPT when an object (e.g., a metal object) is near the WPT system 10; increase the ratio of power delivered by CPT when the alignment between the transmitter resonator 30 and the receiver resonator 50 deteriorates; and / or any combination of the foregoing.

[0196] In some embodiments, the transmission mode ratio can be adjusted according to a maximum power point tracking technique, such as, but not limited to, "observation and disturbance" as sometimes used for wind turbines and solar panels (e.g., see S. Dehghani, S. Abbasian, and T. Johnson, "Adjustable Load With Tracking Loop to Improve RF Rectifier Efficiency Under Variable RF Input Power Conditions," IEEE Transactions on Microwave Theory and Techniques, Vol. 64, No. 2, pp. 343-352, February 2016). In some embodiments, the transmission mode ratio can be adjusted according to a machine learning algorithm. For example, in some embodiments, if the WPT system 10 determines that the WPT efficiency is unexpectedly low, the WPT system 10 can increase the proportion of power delivered by the CPT (or IPT). If the WPT efficiency is negatively affected by the increased reliance on the CPT (or IPT), the WPT system 10 can reduce the reliance on the CPT (or IPT). This process may be repeated iteratively until a desired / maximum WPT efficiency is achieved.

[0197] Each of the transmitter resonator 30 and the receiver resonator 50 may include a plurality of antennas 80 arranged in various configurations.

[0198] Antenna 80 may include any suitable antenna having high self-inductance and high self-capacitance that is capable of creating both magnetic field 31A and electric field 31B (separately and / or simultaneously) for the purposes of CPT and IPT. Figure 2A , 2B 2C depict non-limiting examples of antennas 80, 180, 280. For purposes herein, a "high self-inductance" is a self-inductance that is large enough to allow the antenna to generate a magnetic field suitable for the purposes of IPT. Similarly, for purposes herein, a "high self-capacitance" is a self-capacitance that is large enough to allow the antenna to generate an electric field suitable for the purposes of CPT.

[0199] Figure 2A Depicts antenna 80 according to some embodiments. Antenna 80 may include any suitable conductive material. For example, antenna 80 may include copper, gold, silver, aluminum, other suitable materials, or combinations thereof. Figure 2A As can be seen, antenna 80 includes an elongated element 80A having a rectangular (e.g., square) cross-section that has been bent or formed into a generally planar rectangular (in the XY plane) coil shape such that adjacent wraps of elongated element 80A are spaced apart by gap 80B. While gap 80B is shown as being generally constant along the length of elongated element 80A, this is not mandatory.

[0200] To increase the self-inductance of antenna 80, the size of gap 80B may be reduced. To increase the self-capacitance of antenna 80, the number of bends (e.g., bends 82A) of elongated element 80A may be increased, the number of corners and edges (e.g., edge 82B) of elongated element 80A may be increased, the length of elongated element 80A may be increased, and / or the thickness 80C of elongated element 80A may be increased.

[0201] Figure 2B Another non-limiting example of an antenna 180 according to some embodiments is depicted. Antenna 180 is substantially similar to first antenna 80, except that elongated element 180A is not bent or formed into a generally planar rectangular coil shape, but is bent or formed into a generally planar sawtooth shape with square corners, such as Figure 2B As with antenna 80, adjacent teeth of elongated element 180A are separated by gaps 180B. Although gaps 180B are shown as being substantially constant along the length of elongated element 180A, this is not mandatory.

[0202] To increase the self-inductance of antenna 180, the size of gap 180B may be reduced. To increase the self-capacitance of antenna 180, the number of bends (e.g., bends 182A) of elongated element 180A may be increased, the number of corners and edges (e.g., edge 182B) of elongated element 180A may be increased, and / or the thickness 180C of elongated element 180A may be increased.

[0203] Figure 2C Another non-limiting example of an antenna 280 according to certain embodiments is depicted. Antenna 280 is substantially similar to first antenna 80, except that elongated element 280A, rather than being bent or formed into a generally planar rectangular coil shape, is bent or formed into a generally planar circular shape (in the XY plane) with hub element 280A, wherein sector elements 280C extend radially outward from hub element 280A. Adjacent sector elements 280C are spaced apart from each other by gaps 280B.

[0204] To increase the self-inductance of antenna 280, the size of gap 280B may be reduced. To increase the self-capacitance of antenna 280, the number of sector elements 280C may be increased, the number of corners and edges (e.g., edge 280a) of hub element 280A and / or sector elements 280C may be increased, and / or the thickness 282C of elongated hub element 280A and / or sector elements 280C may be increased.

[0205] Although Figure 2A , 2B2C depict exemplary non-limiting embodiments of antennas 80, 180, 280, but it should be understood that antennas 80 suitable for many other shapes and configurations may be employed in the resonators described herein. Non-limiting examples of changes that may be made to the antennas shown include: changing the cross-sectional shape of the elongated elements 80A, 180A to non-rectangular (e.g., triangular, circular, hexagonal, etc.); changing the 90° bends 82A, 182A to non-90° or circular; changing the XY plane shape of the first transmitter antenna 80 to non-rectangular or circular; using a non-repeating pattern of bends and corners, etc.

[0206] Although antennas 80, 180, 280 are described and shown herein as being relatively flat or planar (e.g., having substantially no variation in thickness in the Z direction), this is not mandatory. In some embodiments, antennas 80, 180, 280 may have a Figure 3A and 3B . For example, the antenna herein may have a conical spiral shape (not shown). In some embodiments, antenna 80 may have a rectangular conical spiral shape such that the inner winding of antenna 80 is spaced apart from the outer winding of antenna 80 in the Z direction. Such a conical shape may allow the resonator to be used for a wider range of resonant frequencies. In other embodiments, the thickness of the first transmitter antenna in the Z direction may vary in other ways.

[0207] For example, the antennas 80, 180, 280 may be arranged in a configuration similar to that of the panels in a CPT WPT system. For example, in a two-antenna WPT system according to some embodiments, the transmitter resonator 30 may include a first transmitter antenna 32 configured in parallel with a first receiver antenna 52 of the receiver resonator 50, such as in Figure 4A . For the purpose of CPT, the mutual capacitance between the two antennas 32, 52 provides a path for current to flow forward to the receiver side, and the conductive path (e.g., ground) will allow the current to flow back to the transmitter side. For the purpose of IPT, by driving current through the first transmitter antenna 32, a magnetic field 31A is generated that can induce current in the first receiver antenna 52. For the purpose of CPT, a voltage can be applied to the first transmitter antenna 32 to form a potential difference between the first transmitter antenna 32 and the first receiver antenna 52, thereby forming an electric field 31B.

[0208] The first transmitter antenna 32 may include any suitable antenna having high self-inductance and high self-capacitance that is capable of forming both the magnetic field 31A and the electric field 31B (separately and / or simultaneously). For example, the first transmitter antenna may include one of antennas 80, 180, 280, or any other antenna described herein.

[0209] The first receiver antenna 52 may include any suitable antenna having high self-inductance and high self-capacitance that is capable of inducing a current therein by the magnetic field 31A and having a potential difference thereacross due to the electric field 31B (separately and / or simultaneously). In some embodiments, the first receiver antenna 52 may be substantially similar to the first transmitter antenna 32 (e.g., the first receiver antenna 52 may have the same characteristics of any antenna described or illustrated herein or otherwise). In some embodiments, the antennas 32, 52 may be different from one another (e.g., the first transmitter antenna 32 may include the antenna 80, while the first receiver antenna 52 may include the antenna 180).

[0210] In some embodiments, the XY plane area of ​​the first transmitter antenna 32 is smaller than the XY plane area of ​​the first receiver antenna 52 to improve coupling between the first transmitter antenna 32 and the first receiver antenna 52 .

[0211] Figure 4B Another example of a configuration of antennas 80, 180, 280 is shown. In some embodiments, Figure 4B A four-antenna stacked (or four-antenna vertical) WPT system is shown. Each of the transmitter resonator 130 and the receiver resonator 150 includes two antennas. One antenna of the transmitter resonator 30 and one antenna of the receiver resonator 150 provide a forward path for power, while another antenna of the transmitter resonator 130 and another antenna of the receiver resonator 150 provide a return path for power.

[0212] For the purpose of IPT, a magnetic field is generated by driving current through the transmitter antennas 132, 134 to induce current in the first receiver antenna 152 and the second receiver antenna 154. For the purpose of CPT, a potential difference can be applied between the first antenna 132 and the second antenna 134 to generate an electric field (at Figure 1 31B) shown in FIG, thereby inducing a potential across the first receiver antenna 152 and the second receiver antenna 154.

[0213] As in Figure 4B As shown in , the transmitter resonator 130 includes a first transmitter antenna 132 and a second transmitter antenna 134 separated in the Z direction by a spacer 138 .

[0214] The first transmitter antenna 132 may include any suitable antenna having high self-inductance and high self-capacitance that is capable of forming both the magnetic field 31A and the electric field 31B (separately and / or simultaneously). For example, the first transmitter antenna may include one of antennas 80, 180, 280, or any other antenna described herein.

[0215] The spacer 138 may include any suitable material. For example, the spacer 138 may include air, a dielectric material, a ferrite, or some combination thereof. The spacer 138 may have a dielectric constant selected to change the electric field 31B and / or it may have a permeability selected to change the magnetic field 31A. The spacer 138 may include a high dielectric constant material that increases the capacitance of the transmitter resonator 130. The thickness and planar area of ​​the spacer 138 may depend on the thickness and / or planar area of ​​the first transmitter antenna 132 and the second transmitter antenna 134. In some embodiments, electrical isolation may be desirable and a low dielectric constant material may be employed for the spacer 138 (e.g., for shielding).

[0216] The second transmitter antenna 134 may include any suitable antenna having high self-inductance and high self-capacitance that is capable of forming both the magnetic field 31A and the electric field 31B (separately and / or simultaneously). In some embodiments, the second transmitter antenna 134 may be substantially similar to the first transmitter antenna 132 (e.g., the second transmitter antenna 134 may have the same characteristics of any antenna described or illustrated herein or otherwise). In some embodiments, the first and second transmitter antennas 132, 134 and the first and second receiver antennas 152, 154 may be different from each other (e.g., the first and second transmitter antennas 132, 134 may be similar to the antenna 80, and the first and second receiver antennas 152, 154 may be similar to the antenna 180).

[0217] In some embodiments, the size of the XY plane area of ​​the second transmitter antenna 134 may be different from the XY plane area of ​​the first transmitter antenna 132. In some embodiments, the XY plane area of ​​the second transmitter antenna 134 may be smaller than the XY plane area of ​​the first transmitter antenna 132 to ensure coupling between each pair of antennas. In some embodiments, the XY plane area of ​​the second transmitter antenna 134 may be larger than the XY plane area of ​​the first transmitter antenna 132.

[0218] In certain embodiments, the second transmitter antenna 134 is substantially complementary to the first antenna 132 in size and / or shape such that the first transmitter antenna 132 does not substantially overlap the second transmitter antenna 134 in the Z-direction. Figure 5 A schematic representation of an XZ plane cross section of a portion of the transmitter resonator 130 is depicted, wherein the first transmitter antenna 132 and the second transmitter antenna 134 are each substantially shaped similar to Figure 2BAs can be seen, the portions 132A-1, 132A-2, 132A-3 of the elongated element 132A of the first transmitter antenna 132 overlap with the gaps 134B-1, 134B-2, 134B-3 of the second transmitter antenna 134 in the Z direction (e.g., a line oriented in the Z direction passing through the portion 132A-1 of the elongated element 132A of the first transmitter antenna 132 passes through the gaps 134B-1, 134B-2, 134B-3 of the second transmitter antenna 134). 1), and portions 134A-1, 134A-2, 134A-3 of the elongated element 134A of the second transmitter antenna 134 overlap with the gaps 132B-1, 132B-2, 132B-3 of the first transmitter antenna 132 in the Z direction (e.g., a line oriented in the Z direction passing through portion 134A-1 of the elongated element 134A of the second transmitter antenna 134 passes through the gap 132B-1 of the first transmitter antenna 132). The complementary shapes of the first transmitter antenna 132 and the second transmitter antenna 134 may reduce parasitic energy losses experienced by the transmitter resonator 130. In some embodiments, the first transmitter antenna 132 and the second transmitter antenna 134 may not be completely complementary, but may have one or more complementary portions.

[0219] The receiver resonator 150 includes a first receiver antenna 152 and a second receiver antenna 154 separated in the Z direction by a spacer 158. The first receiver antenna 152 can be substantially similar to any of the antennas 80, 180, 280, or other antennas described herein. The second receiver antenna 154 can also be substantially similar to any of the antennas 80, 180, 280, or other antennas described herein. Like the first transmitter antenna 132 and the second transmitter antenna 134, the first receiver antenna 152 and the second receiver antenna 154 can be complementary (or partially complementary) in size and / or shape.

[0220] In certain embodiments, such as in Figure 4B As shown in , the XY plane area of ​​the first receiver antenna 152 and the second receiver antenna 154 is different from the XY plane area of ​​the first transmitter antenna 132 and the second transmitter antenna 134 in order to adjust the self-inductance or self-capacitance of the receiver resonator 150. For example, in some embodiments, the XY plane area of ​​the first receiver antenna 152 and the second receiver antenna 154 is larger than the XY plane area of ​​the first transmitter antenna 132 and the second transmitter antenna 134, as shown in Figure 2A This XY plane area difference can improve the ability of the receiver resonator 150 to capture more of the magnetic field 31A and / or the electric field 31B.

[0221] Spacer 158 may include any suitable spacer. Spacer 158 may include the same or similar material as spacer 138 or a different material than spacer 138. Spacer 138 may have a smaller Z-direction dimension than spacer 158 to achieve a desired self-capacitance and / or self-inductance. This may effectively change the coupling coefficient of the link between primary side 12 and secondary side 14 and the impedance of primary side 12. Different compensation networks may be used in both primary side 12 and secondary side 14 to accommodate such coupling coefficient and impedance changes.

[0222] with Figure 4C Compared with the four-antenna parallel structure shown in Figure 4B The stacked configuration is more compact in the XY plane. In addition, since all antennas can be centrally aligned, the configuration is robust to angular misalignment. Specifically, when the antennas are circular in shape, angular rotation has no effect on the coupling capacitance. However, compared to Figure 4C Compared with the four-antenna parallel structure shown in Figure 4B The mutual conductance of the stacked configuration can be reduced due to the increased cross-coupling capacitance.

[0223] Figure 4C Another example of a configuration of antennas 80, 180, 280 is depicted. In some embodiments, Figure 4C A four-antenna parallel (or four-antenna horizontal) WPT system is shown. Each of the transmitter resonator 230 and the receiver resonator 250 includes two antennas. One antenna of the transmitter resonator 230 and one antenna of the receiver resonator 250 provide a forward path for power, while the other antenna of the transmitter resonator 230 and the other antenna of the receiver resonator 250 provide a return path for power.

[0224] For the purpose of IPT, a magnetic field is generated by driving current through the first transmitter antenna 232 and the second transmitter antenna 234 of the transmitter to induce current in the first receiver antenna 252 and the second receiver antenna 254. For the purpose of CPT, a potential difference can be formed between the first transmitter antenna 232 and the second transmitter antenna 234 to generate an electric field 31B, thereby inducing a potential across the first receiver antenna 252 and the second receiver antenna 254.

[0225] with Figure 4B Compared to the transmitter resonator 130 and the receiver resonator 150 shown in FIG. 1 , transmitter resonator 230 and receiver resonator 250 having a horizontal antenna arrangement may be desirable in applications where there are constraints on the Z-direction dimensions of the resonators.

[0226] The transmitter resonator 230 includes a first transmitter antenna 232 and a second transmitter antenna 234 separated in the X direction by a spacer 238. By separating the first transmitter antenna 232 from the second transmitter antenna 234 in the X direction, parasitic energy losses can be reduced. The first transmitter antenna 232 and the second transmitter antenna 234 can be substantially similar to the first transmitter antenna 132 and the second transmitter antenna 134, and the spacer 238 can be substantially similar to the spacer 138. As with the transmitter resonator 130, the first transmitter antenna 232 can have a larger XY plane area than the XY plane area of ​​the second transmitter antenna 234 to improve the forward path for power transfer.

[0227] The spacer 238 may include any suitable material. For example, the spacer 238 may include air, a dielectric material, a ferrite, or a combination thereof. The spacer 238 may have a dielectric constant selected to change the electric field 31B and / or it may have a permeability selected to change the magnetic field 31A. The spacer 238 may include a high dielectric constant material that increases the capacitance of the transmitter resonator 230. The thickness and planar area of ​​the spacer 238 may depend on the thickness and / or planar area of ​​the first transmitter antenna 232 and the second transmitter antenna 234. In some embodiments, electrical insulation may be desirable and may be targeted to a low dielectric constant material (e.g., for shielding) employed for the spacer 238.

[0228] The receiver resonator 250 includes a first receiver antenna 252 and a second receiver antenna 254 separated in the X direction by a spacer 258. By separating the first receiver antenna 252 from the second receiver antenna 254 in the X direction, parasitic energy losses can be reduced. The first receiver antenna 252 and the second receiver antenna 254 can be substantially similar to the first receiver antenna 152 and the second receiver antenna 154, and the spacer 258 can be substantially similar to the spacer 138. As with the receiver resonator 150, the first receiver antenna 252 can have a larger XY plane area than the XY plane area of ​​the second receiver antenna 254.

[0229] Spacer 258 may include any suitable spacer. Spacer 258 may include the same or similar material as spacer 238 or a different material from spacer 238. Spacer 238 may have a smaller Z-direction dimension than spacer 258 to achieve a desired self-capacitance and / or self-inductance. This may effectively change the coupling coefficient of the link between primary side 12 and secondary side 14 and the impedance of primary side 12. Different compensation networks may be used in both primary side 12 and secondary side 14 to accommodate such coupling coefficient and impedance changes.

[0230] In some embodiments, the XY plane area of ​​the spacer 258 may be different than the XY plane area of ​​the spacer 238 in order to vary the self-inductance or self-capacitance of the transmitter resonator 230 or the receiver resonator 250. For example, the spacer 238 may have a smaller XY plane area than the spacer 258, as shown.

[0231] Figure 4D Another example of a configuration of antennas 80, 180, 280 is depicted. In some embodiments, Figure 4D Describe and Figure 4B Stack configuration and Figure 4C The six-antenna WPT system of the parallel configuration combination. Each of the transmitter resonator 130 and the receiver resonator 150 includes three antennas. One of the first transmitter antenna 332 and the second transmitter antenna 334 and one of the first receiver antenna 352 and the second receiver antenna 354 provide a forward path for power together, and the other of the first transmitter antenna 332 and the second transmitter antenna 334 and the other of the first receiver antenna 352 and the second receiver antenna 354 provide a return path for power together. The third transmitter antenna 336 and the third receiver antenna 356 operate as auxiliary antennas to increase the equivalent self-capacitance and act as an electric field shield. In some embodiments, the third transmitter antenna 336 and the third receiver antenna 356 are passive (for example, no potential difference is applied between the third transmitter antenna 336 and the third receiver antenna 356 and / or no current is driven through the third transmitter antenna 336 and the third receiver antenna 356). For the purpose of IPT, a magnetic field that can induce current in the first receiver antenna 352, the second receiver antenna 354, and the third receiver antenna 356 is generated by driving current through one or more of the first transmitter antenna 332, the second transmitter antenna 334, and the third transmitter antenna 336 of the transmitter. For the purpose of CPT, a voltage can be applied to the first transmitter antenna 332, the second transmitter antenna 334, and / or the third transmitter antenna 336 to form a potential difference between any of the first transmitter antenna 332, the second transmitter antenna 334, and the third transmitter antenna 336, thereby forming an electric field 31B.

[0232] The transmitter resonator 330 includes a first transmitter antenna 332 and a second transmitter antenna 334 separated in the X direction by a spacer 338, and a third transmitter antenna 336 separated from the first and second transmitter antennas and the spacer 338 by a second spacer 339. The third transmitter antenna 336 may provide electric field shielding to reduce undesired escape of electric fields from the transmitter resonator 330. The third transmitter antenna 336 may contain a ferrite sheet or surface to provide magnetic field shielding to reduce undesired escape of magnetic fields from the transmitter resonator 330. By varying the spacer 339, shielding or shaping of electric or magnetic fields is also possible.

[0233] The first transmitter antenna 332, the second transmitter antenna 334, and the third transmitter antenna 336 may be substantially similar to either of the first transmitter antenna 132 and the second transmitter antenna 134. The spacers 338, 339 may be substantially similar to the spacer 138. As with the transmitter resonator 130, the first transmitter antenna 332 may have a larger XY plane area than the XY plane area of ​​the second transmitter antenna 334. The third transmitter antenna 336 may have a larger XY plane area than either of the first transmitter antenna 332 and the second transmitter antenna 334.

[0234] The spacers 338, 339 may include any suitable material. For example, the spacers 338, 339 may include air, a dielectric material, a ferrite, or a combination thereof. The spacers 338, 339 may have a dielectric constant selected to change the electric field 31B and / or they may have a permeability selected to change the magnetic field 31A. The spacers 338, 339 may include a high dielectric constant material to increase the capacitance of the transmitter resonator 230. The thickness and planar area of ​​the spacers 338, 339 may depend on the thickness and / or planar area of ​​the first transmitter antenna 332, the second transmitter antenna 334, and the third transmitter antenna 336. In some embodiments, electrical isolation may be desirable, and a low dielectric constant material may be employed for the spacers 338, 339 (e.g., for shielding).

[0235] The receiver resonator 350 includes: a first receiver antenna 352 and a second receiver antenna 354 separated in the X direction by a spacer 358; and a third receiver antenna 356 separated from the first receiver antenna, the second receiver antenna and the spacer 358 by a second spacer 359. The third receiver antenna 356 can provide electric field shielding to reduce the undesired escape of electric fields from the receiver resonator 350. The third receiver antenna 356 can contain a ferrite sheet or surface to provide magnetic field shielding to reduce the undesired escape of magnetic fields from the transmitter. By changing the spacer 359, shielding or shaping of electric or magnetic fields is also possible. The first receiver antenna 352, the second receiver antenna 354 and the third receiver antenna 356 can be substantially similar to any of the first receiver antenna 152 and the second receiver antenna 154. The spacers 358, 359 can be substantially similar to the spacer 158. As with the receiver resonator 150, the first receiver antenna 352 can have a larger XY plane area than the XY plane area of ​​the second receiver antenna 354. The third receiver antenna 356 may have a larger XY plane area than either of the first receiver antenna 352 and the second receiver antenna 354 .

[0236] Spacers 358, 359 may include any suitable spacers. Spacers 358, 359 may include the same or similar materials as spacers 338, 339 or different materials from spacers 338, 339. Spacers 338, 339 may have a smaller Z-direction dimension than spacers 358, 359 to achieve the desired self-capacitance and / or self-inductance. This may effectively change the coupling coefficient of the link between the primary side 12 and the secondary side 14 and the impedance of the primary side 12. Different compensation networks may be used in both the primary side 12 and the secondary side 14 to accommodate such coupling coefficient and impedance changes.

[0237] In some embodiments, the XY plane area of ​​the spacer 358 may be different from the XY plane area of ​​the spacer 338 in order to vary the self-inductance or self-capacitance of the transmitter resonator 330 or the receiver resonator 350. For example, the spacer 338 may have a smaller X-direction dimension than the spacer 358. In some embodiments, the Z-direction dimension of the spacer 359 may be different from the Z-direction dimension of the spacer 339 in order to vary the self-inductance or self-capacitance of the transmitter resonator 330 or the receiver resonator 350. For example, the spacer 339 may have a smaller Z-direction dimension than the spacer 359. This may effectively change the coupling coefficient of the path between the primary side 12 and the secondary side 14 and the impedance of the primary side 12. Different compensation networks may be used in both the primary side 12 and the secondary side 14 to accommodate such coupling coefficient and impedance changes.

[0238] In some embodiments, a magnetic shield may be provided around one or more of the transmitter resonator 30 and the receiver resonator 50. For example, ferrite may be used as a magnetic shield and to reduce undesirable eddy currents in nearby metal objects. Ferrite (or another suitable material) may also be employed to isolate the transmitter resonator 30 and / or the receiver resonator 50 from surrounding metal objects and may therefore be used to increase the self-inductance of the antenna and / or the mutual inductance of the resonators.

[0239] Figure 6 A schematic diagram of the primary side 12 including a transmitter module 20 and a transmitter resonator 30 is depicted in accordance with certain embodiments. The transmitter resonator 30 may include any of the transmitter resonators 30, 130, 230, 330, or other transmitter resonators described herein.

[0240] The transmitter module 20 includes a controller 22. The controller 22 is configured to receive various inputs from sensors 24 (e.g., load detector 24A, transmitter power sensor 24B, surrounding object detector 24C, and / or distance detector 24D) and output control signals to various components 26 (e.g., oscillator 26A, power amplifier 26B, filter network 26C, matching network 26D, compensation network 26E, and V / I tuner 26F).

[0241] The load detector 24A is configured to detect a load 70 (shown in FIG. Figure 7 The load 70 may be a battery for an electric vehicle, such as an electric bicycle or electric car, or any other suitable item requiring power input. The load detector 24A may be implemented with a physical sensor, such as, without limitation, an optical sensor, a pressure sensor, an infrared sensor, or a proximity sensor, and suitable software or firmware. For example, in some embodiments, power (e.g., current and voltage) is measured at, for example, point 24E to determine the power drawn by the transmitter resonator 30 (e.g., as measured by the transmitter power sensor 24B). If the amount of power drawn by the transmitter resonator 30 increases above a baseline, the load detector 24A may signal the presence of the load 70 to the controller 22.

[0242] In other embodiments, the load detector 24A may be configured to measure the input impedance of the transmitter resonator 30 as seen by the transmitter module 20 at point 24E. The presence of a resonant load in proximity to the transmitter resonator 30 (including, for example, the secondary side 14 configured to drive the load 70) will change the input impedance of the transmitter resonator 30. The change in impedance provided to the controller 22 by the load detector 24A may be used by the transmitter controller 22 to determine whether a cooperating receiver is in proximity to the transmitter resonator 30. The impedance changes induced in the transmitter resonator 30 by different receivers are different and characteristic, making it possible for the controller 22 to not only detect the presence or absence of a receiver in proximity to the transmitter resonator 30, but also to identify the type of receiver, such as, for example, different models of cell phones or digital tablets, including without limitation.

[0243] The transmitter power sensor 24B may measure the power at point 24E (e.g., measure current and voltage) to determine how much power is being drawn by the transmitter resonator 30. This information may be used, for example, by the load detector 24A to determine whether there is a desirably efficient coupling between the transmitter resonator 30 and the receiver resonator 50.

[0244] The surrounding object detector (SOD) 24C is configured to determine whether an object (e.g., a living being such as a person or animal, or a static object such as a piece of metal or other) is in proximity to the transmitter resonator 30. The SOD 24C may be implemented with a physical sensor (e.g., without limitation, an optical sensor, a pressure sensor, an infrared sensor, a proximity sensor, a radar, or a lidar) or by suitable software or firmware. For example, if the power drawn by the transmitter resonator 30 (as measured by the transmitter power sensor 24B) drops during the IPT, the software of the SOD may determine that a piece of metal (or any electrical conductor) is in proximity to the transmitter resonator 30 or the receiver resonator 50, and the SOD may provide a signal to the controller 22 indicating this presence. In certain embodiments, if a metal object is detected in proximity to the transmitter resonator 30 or the receiver resonator 50, the controller 22 may cause the transmitter module 20 to increase the proportion of power delivered by the CPT. In the event that the absence of a living being is detected by the SOD 24C, the controller 22 may be configured to increase the power feed to the transmitter resonator 30 (e.g., above the regulated level in the event that a living being is present), or in the event that the approach of a living being is detected by the SOD 24C, the controller 22 may be configured to reduce the power feed to the transmitter resonator 30 below the regulated level.

[0245] The distance detector 24D is configured to determine the distance between the transmitter resonator 30 and the receiver resonator 50. The distance detector 24D may be implemented with a physical sensor (e.g., without limitation, an optical sensor, an ultrasonic sensor, an infrared sensor, a proximity sensor, a radar, or a lidar) or by suitable software or firmware. For example, the distance detector 24D may be configured to determine the distance between the transmitter resonator 30 and the receiver resonator 50 based on the change in the transmission power measured by the transmitter power sensor 24B.

[0246] In one embodiment, one or more temperature sensors may monitor the temperature at the transmitter resonator 30 or the receiver resonator 50. If the temperature exceeds a predetermined limit, the controller 22 may cause the transmitter module 20 to reduce the proportion of power delivered by the IPT, reduce the total power feed to the transmitter resonator 30, or shut down power to the transmitter resonator 30 to prevent a fire hazard or thermal runaway.

[0247] The oscillator 26A may be configured to control the frequency band and / or bandwidth and / or duty cycle (phase) (eg, 5% to 50%) of the current delivered to the transmitter resonator 30 in response to a signal from the controller 22 .

[0248] The power amplifier 26B may be employed to convert the DC power into AC power. The power amplifier 26B may be employed to adjust the power provided to the transmitter resonator 30 in response to a signal from the controller 22. In some embodiments, the controller 22 may send a signal to the power amplifier 26B to adjust the reflection coefficient of the power amplifier 26B. In some embodiments, when the load detector 24A does not detect a load, the controller 22 may send a signal to the power amplifier 26B to turn off (or sleep), or when the load detector 24A detects a load, the controller 22 may send a signal to the power amplifier 26B to turn on.

[0249] The power amplifier 26B may include a switched mode power amplifier (in either a single-ended mode or a differential configuration) that may be configured to receive a square wave (sine wave) from the oscillator 26A and generate a sine wave of a particular frequency desired to drive the transmitter resonator 30 . Figure 8 is a schematic diagram of an exemplary power amplifier 26B that can be used in the transmitter 30. The power amplifier 26B can be a differential switching mode amplifier. The power amplifier 26B has three inputs, namely: two input signals that drive active devices (transistors) 127C, 127D at a frequency set at the resonant frequency and a DC voltage source 127E for controlling the output power and operating region of the active devices.

[0250] Different load terminations are used to improve performance (e.g., output power, power conversion efficiency) and reduce unnecessary harmonic levels. In some embodiments, the third harmonic termination 127F is located in the series branch to shape the voltage waveform at the drain node 127G. The second harmonic termination 127H is located in the parallel branch to shape the voltage waveform at the drain node 127G. The first harmonic termination 127I is located in the series branch to shape the voltage waveform at the drain node 127G. The effect of the third harmonic termination can be considered in the second harmonic termination 127H and the first harmonic termination 127I. The effect of the second harmonic termination 127H can be considered in the first harmonic termination 127I. For the differential configuration of the power amplifier 26B, the AC load 127J (which receives the output power) is placed in series. The charging rate of the AC load 127J can be a function of the alignment and position of the transmitter resonator 30, the receiver resonator 50, and / or the like. The power amplifier 26B may be configured to generate sufficient power for the transmitter resonator 30 so that an E field, or an H field, or any combination of E and H fields may be generated by the transmitter resonator 30 and captured by the receiver resonator 50 .

[0251] The power amplifier 26B may include two phase shifters 127L in a differential configuration (but only one phase shifter in a single-ended configuration). The phase shifter 127L adjusts the appropriate phase difference between the AC signal overload 127J and the gate signal of the transistors 127C, 127D. The phase difference between the gate signal and the AC signal overload 127J may change the performance of the power amplifier, such as the power conversion efficiency and operating region of the transistors. It may also change the output impedance of the transistors 127C and 127D and / or the optimal AC load 127J of the power amplifier 26B.

[0252] The power amplifier 26B may include two level shifters 127K in a differential configuration (but only one level shifter in a single-ended configuration). The level shifter 127K may adjust the appropriate amplitude of the gate signal of the transistors 127C, 127D. The amplitude level at the gate signal may change the performance of the amplifier (e.g., the power conversion efficiency and operating region of the transistor).

[0253] The power amplifier 26B may be reconfigurable to function as a rectifier, and in some embodiments as a self-synchronous rectifier. As part of this reconfiguration, the integrated phase shifter 127L and the integrated level shifter 127K may be adjusted based on the inherent amplification and switching functions of the transistors 127C, 127D (see Figure 8) to allow the power amplifier 26B to function as a rectifier. The reconfigurability of the power amplifier 26B between operating as an amplifier and operating as a rectifier allows the transmitter module 20 to be controllably reconfigured between a transmitter mode and a receiver mode, respectively. The reconfiguration may occur under instructions from the controller 22. When the power amplifier 26B is reconfigured from an amplifier to a rectifier, the AC load 127J changes to an AC source 127J. Accordingly, when the power amplifier 26B is reconfigured from an amplifier to a rectifier, the DC source 127E is reconfigured to a DC load. Having described the secondary side 14 and its receiver module (both of which are in Figure 7 The use of the transmitter module 20 in its receiver mode will be discussed below, after being shown in more detail in FIG.

[0254] The filter network 26C can adjust the frequency response, such as bandwidth, cutoff frequency, 3dB frequency, and gain provided to the transmitter resonator 30 in response to the signal from the controller 22. The filter network 26C can be configured to adjust the waveform shape of the power in the transmitter module 20 to increase the efficiency of the transmitter module 20.

[0255] The matching network 26D may be configured to adjust the impedance to match the output of the power amplifier 26B to the transmitter resonator 30 .

[0256] A compensation network 26E may be provided to drive the transmitter resonator 30 at a desired resonant frequency (e.g., the resonant frequency of the receiver resonator) to increase mutual flux, reduce heat generation, and improve power transfer efficiency. The compensation network 26E may include one or more capacitors for increasing capacitance and one or more inductors for increasing inductance. The compensation network 26E may be configured to increase capacitance (and / or decrease inductance) and increase inductance (and / or decrease capacitance) as desired. When the transfer mode ratio is 100% CPT, the compensation network 26E may function in a manner similar to any known CPT compensation network (e.g., the compensation network 26E may function to increase inductance). Similarly, when the transfer mode ratio is 100% IPT, the compensation network 26E may function in a manner similar to any known IPT compensation network (e.g., the compensation network 26E may function to increase capacitance). However, when the transmit mode is partial CPT and partial IPT, less compensation may be required because the capacitance of the transmitter resonator 30 will naturally provide compensation for the inductance of the transmitter resonator 30 and the inductance of the transmitter resonator 30 will naturally provide compensation for the capacitance of the transmitter resonator 30. For example, at approximately 50% IPT and 50% CPT (e.g., the transmit mode ratio is equal to 1), the compensation network may not be required at all or its use may be substantially limited, thereby increasing the efficiency of the WPT system 10.

[0257] As another example, between approximately 40% to 60% IPT and 40% to 60% CPT, a compensation network may not be needed at all or its use may be substantially limited, thereby increasing the efficiency of the WPT system 10. For this reason, the compensation network 26E may include fewer or smaller inductors and / or capacitors than a CPT WPT system and / or a pure IPT WPT system that require significant compensation. In certain embodiments, if the capacitance of the transmitter resonator 30 is significantly low, additional compensation may be provided by the compensation network 26E. Similarly, if the inductance of the transmitter resonator 30 is significantly low, additional compensation may be provided by the compensation network 26E. For example, the controller 22 may signal to the compensation network 26E how much and what type of compensation is needed based on the transmit mode ratio, the distance between the transmitter resonator 30 and the receiver resonator 50, the amount of power drawn by the transmitter resonator 30, the power transmission efficiency, etc.

[0258] In certain embodiments, the amount of compensation (e.g., capacitance increase or inductance increase) performed by the compensation network 26E is proportional to the absolute value of the difference between the transfer mode ratio and 1. For example, if the transfer mode ratio is greater than 1, the compensation network 26E may act to increase the inductance, and the amount of increase in inductance may increase as the transfer mode ratio increases above 1. Similarly, if the transfer mode ratio is less than 1, the compensation network 26E may act to increase the capacitance, and the amount of increase in capacitance may increase as the transfer mode ratio decreases below 1.

[0259] In some embodiments, the compensation network 26E can be configured to modulate the signal provided to the transmitter resonator 30 with information and can thereby act as a source transmission modulator. The information used to modulate the signal provided to the transmitter resonator 30 can be provided to the compensation network 26E by the controller 22. The information can include control data that is sent to the controller 42 of the receiver module 40 via the receiver resonator 50. Figure 7Controller 42 is described in more detail. In other embodiments, power amplifier 26B may act as a source transmission modulator. In still further embodiments, oscillator 26A may act as a source transmission modulator. The modulation employed by the selected source transmission modulator may be any of amplitude modulation, frequency modulation, and phase modulation. Information may be modulated onto the signal provided to the transmitter resonator 30 in digital form or in analog form. Information may be modulated onto the resonant frequency of the power signal provided to the transmitter resonator 30 by the source transmission modulator. In other embodiments, the information may be modulated onto a frequency different from the frequency of the power transmission. In other embodiments, the information may be modulated onto a harmonic of the resonant frequency of the power signal provided to the transmitter resonator 30. In still further embodiments, the resonant frequency of the power signal provided to the transmitter resonator 30 may be a harmonic of the frequency of the signal onto which the information is modulated. V / I tuner 26F, described in more detail below, may be configured to transmit an information signal to the transmitter resonator 30 and thereby be transparent to the information being transmitted. Information transmitted in the manner described herein may include, without limitation, the operating mode of module 20, the number and type of receiver modules 40, surrounding object sensor information, and load status monitoring information including, for example, battery charge status, load voltage, and load current.

[0260] exist Fig.10 An embodiment of the V / I tuner 26F is shown in more detail in FIG. Figure 6 The input signal of the V / I tuner 26F received in the above embodiment is separated by the separator 262 so as to have two mutually asymmetric paths 261A and 261B for the input signal. The first phase shifter 264A and the second phase shifter 264B form the transmitter resonator 30 (in the above embodiment). Figure 6 The first phase shifter 264A is controlled by the controller 22 (in Figure 6 ) is controlled via the first phase splitter control line 263A, while the second phase shifter 264B is controlled by the controller 22 (see Figure 6) is controlled via the second phase splitter control line 263B. The first active switch 266A and the second active switch 266B receive signals from the first phase shifter 264A and the second phase shifter 264B, respectively, and are controlled by the controller 22 via the first active switch control line 265A and the second active switch control line 265B, respectively. The first active switch 266A and the second active switch 266B are used to adjust the imaginary part of the signal received from the first phase shifter 264A and the second phase shifter 264B, respectively. The passive signal shaping networks 268A and 268B receive the adjusted signals from the first active switch 266A and the second active switch 266B, respectively. The passive signal shaping networks 268A and 268B are used to fine tune the signals received from the first active switch 266A and the second active switch 266B, respectively, and in some embodiments, to reduce any harmonics in those signals before passing them to the combiner 269. The signals provided along the two mutually asymmetric paths 261A and 261B are combined by the combiner 269 and provided to the transmitter resonator 30. In other embodiments, the first phase shifter 264A and the second phase shifter 264B may be combined into one phase shifter that receives the input signal to the V / I tuner 26F, and the combined phase shifter may have two separate outputs that serve the active switches 266A and 266B.

[0261] The V / I tuner 26F adjusts the transmit mode ratio by adjusting the phase difference between the input current and the input voltage of the transmitter resonator 30 in response to a signal from the controller 22. The real part of the impedance seen by the transmitter module 20 is adjusted by the phase shifters 264A and 264B, and the imaginary part can be adjusted by the active switches 266A and 266B. For example, a 90 degree phase shift every 3 milliseconds out of every 10 milliseconds can result in 30% magnetic force transmission and 70% power transmission.

[0262] The V / I tuner 26F may be configured to adjust the current passing through each transmitter antenna (e.g., the first transmitter antenna 32, 132, 232, 332 and the second transmitter antenna 134, 234, 334 or the third transmitter antenna 336) and the potential applied to each transmitter antenna (e.g., the first transmitter antenna 32, 132, 232, 332 and the second transmitter antenna 134, 234, 334 or the third transmitter antenna 336).

[0263] If current is caused to pass through both the first transmitter antenna 132 and the second transmitter antenna 134, the transmitter antennas will each generate a magnetic field 31A for the purpose of IPT. If the current delivered to the second transmitter antenna 134 is reduced compared to the current delivered to the first transmitter antenna 132, a potential difference will be generated between the first transmitter antenna 132 and the second transmitter antenna 134 for the purpose of CPT and an electric field 31B will be generated. In order to modulate between CPT and IPT, the current delivered to the second antenna 134 can be modulated (e.g., when less current is allowed to pass through the second antenna 134, less IPT will occur, and when more current is allowed to pass through the second antenna, more CPT will occur). For example, when it is desired to transmit power via IPT, the I / V tuner 26F can be configured to act as a short circuit connecting the first transmitter antenna and the second transmitter antenna together to thereby form a series LC resonator that allows current to flow therein. Conversely, when it is desired to transmit power via CPT, the I / V tuner 26F can be configured to act as an open circuit to dump current, thereby creating a potential difference between the first transmitter antenna and the second transmitter antenna. The I / V tuner 26F can thus be configured to control whether the first transmitter antenna 132 and the second transmitter antenna 134 are effectively connected in series or in parallel.

[0264] Alternatively, when the first transmitter antenna 132 and the second transmitter antenna 134 are connected in parallel, the first transmitter antenna 132 and the second transmitter antenna 134 may be floating to cause the electric field 31B to be generated for the purpose of CPT without substantially generating the magnetic field 31A. To change the transmit mode ratio (e.g., to modulate between CPT and IPT), the I / V tuner 26F may be configured (via a multiplexer of the I / V tuner 26F, etc.) to alternate between: (1) floating the first transmitter antenna 132 and the second transmitter antenna 134 to cause CPT; and (2) driving current through the first transmitter antenna 132 and the second transmitter antenna 134 to cause IPT. The alternation may be implemented in milliseconds or at a frequency between 10 Hz and 10 kHz. With more time allocated to floating the first and second transmitter antennas 132, 134, the transmit mode ratio will be biased toward achieving more CPT, and with more time allocated to driving current through the first and second transmitter antennas 132, 134, the transmit mode will be biased toward achieving more IPT.

[0265] In some embodiments, elements 26 may be discrete components in transmitter module 20, while in other embodiments, one or more of elements 26 may be part of an integrated circuit design.

[0266] Figure 7is a load 70 according to some embodiments and a secondary side 14 including a receiver resonator 50 and a receiver module 40 (such as in Figure 1 Schematic drawing of ).

[0267] The receiver resonator 50 may include any of the receiver resonators 50, 150, 250, 350, or other receiver resonators described herein. The receiver resonator 50 may be configured to capture power at a frequency set by the oscillation signal in the transmitter module 20 (e.g., without limitation, such as between 1 MHz and 1 GHz). In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is about 1 MHz to about 100 MHz, about 1 MHz to about 200 MHz, about 1 MHz to about 300 MHz, about 1 MHz to about 400 MHz, about 1 MHz to about 500 MHz, about 1 MHz to about 600 MHz, about 1 MHz to about 700 MHz, about 1 MHz to about 800 MHz, about 1 MHz to about 900 MHz, about 1 MHz to about 1 GHz, about 100 MHz to about 200 MHz, about 100 MHz to about 300 MHz, about 100 MHz to about 400 MHz, about 10 0 MHz to about 500 MHz, about 100 MHz to about 600 MHz, about 100 MHz to about 700 MHz, about 100 MHz to about 800 MHz, about 100 MHz to about 900 MHz, about 100 MHz to about 1 GHz, about 200 MHz to about 300 MHz, about 200 MHz to about 400 MHz, about 200 MHz to about 500 MHz, about 200 MHz to about 600 MHz, about 200 MHz to about 700 MHz, about 200 MHz to about 800 MHz, about 200 MHz to about 900 MHz, about 200 MHz to about 1 GHz, about 300 MHz to about 400 MHz, about 300 MHz to about 500 MHz, about 300 MHz to about 600 MHz, about 300 MHz to about 700 MHz, about 300 MHz to about 800 MHz, about 300 MHz to about 900 MHz, about 300 MHz to about 1 GHz, about 400 MHz to about 500 MHz, about 400 MHz to about 600 MHz, about 400 MHz to about 700 MHz, about 400 MHz to about 800 MHz, about 400 MHz to about 900 MHz, about 400 MHz to about 1 GHz, about 500 MHz to about 600 MHz. Hz, about 500 MHz to about 700 MHz, about 500 MHz to about 800 MHz, about 500 MHz to about 900 MHz, about 500 MHz to about 1 GHz, about 600 MHz to about 700 MHz, about 600 MHz to about 800 MHz, about 600 MHz to about 900 MHz, about 600 MHz to about 1 GHz, about 700 MHz to about 800 MHz, about 700 MHz to about 900 MHz, about 700 MHz to about 1 GHz, about 800 MHz to about 900 MHz, about 800 MHz to about 1 GHz, or about 900 MHz to about 1 GHz.In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is about 1 MHz, about 100 MHz, about 200 MHz, about 300 MHz, about 400 MHz, about 500 MHz, about 600 MHz, about 700 MHz, about 800 MHz, about 900 MHz, or about 1 GHz. In some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is at least about 1 MHz, about 100 MHz, about 200 MHz, about 300 MHz, about 400 MHz, about 500 MHz, about 600 MHz, about 700 MHz, about 800 MHz, or about 900 MHz. In some embodiments, in some embodiments, the frequency set by the oscillation signal in the transmitter module 20 is at most about 100 MHz, about 200 MHz, about 300 MHz, about 400 MHz, about 500 MHz, about 600 MHz, about 700 MHz, about 800 MHz, about 900 MHz, or about 1 GHz.

[0268] For some applications, frequencies in the Industrial, Scientific and Medical (ISM) band may be preferred. For purposes of the present invention, the ISM band is understood to be 6.765 MHz to 6.795 MHz; 13.553 MHz to 13.567 MHz; 26.957 MHz to 27.283 MHz; 40.66 MHz to 40.70 MHz; 83.996 MHz to 84.004 MHz; 167.992 MHz to 168.008 MHz; 433.05 MHz to 434.79 MHz; and 886 MHz to 906 MHz. For other applications, frequencies in officially reserved application bands may be preferred, such as, without limitation, police communications or military bands. The receiver resonator 50 may be configured to capture power at that frequency from the magnetic field 31A or the electric field 31B, or any combination of the two fields.

[0269] Receiver module 40 includes controller 42. Controller 42 is configured to receive various inputs from sensors 44 (e.g., receiver power sensor 44A and load detector 44B) and output control signals to various elements 46 (e.g., compensation network 46A, matching network 46B, rectifier 46D, filter 46C, and load manager 46E).

[0270] The receiver power sensor 44A may measure the power at point 44C (eg, measure current and voltage) to determine how much power the receiver resonator 50 is receiving.

[0271] The load detector 44B is configured to detect the presence of the load 70. The load detector 44B may be implemented with a physical sensor (e.g., without limitation, an optical sensor, a pressure sensor, an infrared sensor, or a proximity sensor) or by suitable software or firmware. For example, in some embodiments, the current and voltage at, for example, point 44D are measured by the load detector 44B to determine the power received by the load 70. If the amount of power measured at point 44D increases above a baseline, the load detector 44B signals the controller 42 that the load 70 is present.

[0272] The compensation network 46A may be configured to maintain a desired resonant frequency of the receiver resonator 50 in response to a signal from the controller 42, thereby improving the efficiency of power transfer from the transmitter resonator 30 to the receiver resonator 50. The compensation network 46A may be similar to the compensation network 26E of the transmitter module 20 and may function substantially the same as the compensation network 26E of the transmitter module 20.

[0273] The matching network 26D may be configured to adjust the input impedance of the rectifier 46D to match the desired impedance of the transmitter resonator 30 for maximum power transfer.

[0274] The rectifier 46D may be configured to convert AC power received by the receiver antenna 50 into DC power to be provided to the load 70 .

[0275] The filter 46C may be configured to shape the waveform of the power output from the rectifier 46D according to a signal from the controller 42 in order to improve the overall power efficiency of the receiver module 40 .

[0276] Load manager 46E may be configured to provide a suitable voltage and current to load 70 and / or extract maximum power from rectifier 46D by adjusting its input impedance (eg, output impedance of rectifier 46D).

[0277] In certain embodiments, the load manager 46E or another component may be configured to communicate (wirelessly or wired) with an external device (e.g., the load 70) to provide appropriate information for data analysis. For example, without limitation, this information may include: the presence of the load 70, the charge level of the load 70, the charge rate of the load 70, the state of the load 70, the current voltage, capacity, and / or the remaining time to charge the load 70. The load manager 46E may use the information (or relay the information to the controller 42 or controller 22) to adjust, for example, the transfer mode ratio to achieve optimal energy transfer between the primary side 12 and the secondary side 14. The load manager 46E may also provide the information to the user via a display. The display may be built into one or more of the primary side 12 and the secondary side 14 or may be accessed via software on a mobile device (such as, for example, an application on a mobile phone or tablet computer that communicates wirelessly (or wired) with the load manager 46E or the controller 22 or controller 42).

[0278] In some embodiments, components 46 are discrete elements in receiver module 40, while in other embodiments, one or more of components 46 are part of an integrated circuit design.

[0279] In some embodiments, the primary side 12 may include multiple transmitter resonators 30, and / or the secondary side 14 may include multiple receiver resonators 50. In such embodiments, each of the transmitter resonators 30 and / or the receiver resonators 50 may be controlled in a similar manner. In other embodiments, each of the transmitter resonators 30 and / or the receiver resonators 50 may be controlled individually. For example, in some embodiments, the primary side 12 may rely more heavily on transmitter resonators 30 that experience less interference (e.g., due to nearby metal objects), are not near living beings, or transmit power more efficiently and / or similarly, and the secondary side 14 may rely more heavily on receiver resonators 50 that experience less interference (e.g., due to nearby metal objects), are not near living beings, or receive power more efficiently. For example, this control may be provided or facilitated by the transmitter module 20 and the receiver module 40 and / or the communication therebetween.

[0280] Fig. 9 is a schematic depiction of a rectifier 46D having an integrated phase shifter. In certain embodiments, the rectifier 46D includes a discrete phase shifter.

[0281] The rectifier 46D may be a switched mode self-synchronous rectifier (in a single-ended mode or a differential configuration) that may be configured to receive a sine wave (e.g., AC power) from the receiver resonator 50 at a particular resonant frequency. The rectifier 46D may be a differential switched mode self-synchronous rectifier. The rectifier 46D may capture enough power from the receiver resonator 50 so that the E field, or the H field, or any combination of the E field and the H field may be captured by the receiver resonator 50.

[0282] Rectifier 46D has an input 147A (e.g., AC power) that drives an active device 147B (e.g., a transistor) with a frequency set at the resonant frequency and has an output 147D (e.g., a DC voltage) across a DC load (for controlling the output power, input impedance, and operating region of the active device). In this design, different load terminations are used to improve performance (e.g., output power and power conversion efficiency). The third harmonic termination 147D is located in the series branch to shape the voltage waveform at the drain node 147E. The second harmonic termination 147F is located in the parallel branch to shape the voltage waveform at the drain node 147E. The first harmonic termination 147G is located in the series branch to shape the voltage waveform at the drain node 147E. The effect of the third harmonic termination 147D can be considered in the second harmonic termination 147F and the first harmonic termination 147G. The effect of the second harmonic termination 147F can be considered in the first harmonic termination 147G.

[0283] For the differential configuration, the AC source 147A is placed in series. The AC source 147A may be a function of the power received by the receiver resonator 50 and the alignment and position of the receiver resonator 50 relative to the transmitter resonator 30. The DC load 147C may be a single ended load.

[0284] The rectifier 46D may include two phase shifters 147H in a differential configuration (but only one phase shifter in a single-ended configuration). The phase shifter 147H adjusts the appropriate phase difference between the AC source and the gate signal of the transistor 147B. The phase difference between the gate signal and the AC source 147A may change the performance of the self-synchronous rectifier (e.g., the power conversion efficiency and operating region of the transistor). It may also change the input impedance of the self-synchronous rectifier 46D and / or the optimal DC load 147C of the rectifier 46D.

[0285] Rectifier 46D may include two level shifters 147I in a differential configuration (but only one level shifter in a single-ended configuration). Level shifter 147I may adjust the appropriate amplitude of the gate signal of transistor 147B. The amplitude level at the gate signal may change the performance of the self-synchronous rectifier (e.g., the power conversion efficiency and operating region of the transistor).

[0286] The rectifier 46D may be reconfigurable to function as an amplifier. As part of this reconfiguration, the integrated phase shifter 147H and the integrated level shifter 147I may be adjusted (see Fig. 9 ), so as to allow rectifier 46D to function as an amplifier based on the inherent amplification and switching functions of transistor 147B. The reconfigurability of rectifier 46D between operating as a rectifier and operating as an amplifier allows receiver module 40 to be controllably reconfigured between a receiver mode and a transmitter mode, respectively. The reconfiguration may occur under instructions from controller 42. When rectifier 46D is reconfigured from a rectifier to an amplifier, AC source 147A changes to AC load 147A. Accordingly, when rectifier 46D is reconfigured from a rectifier to an amplifier, DC load 147C is reconfigured to a DC source.

[0287] In some embodiments, when the receiver module 40 is in the transmitter mode, the compensation network 46A can be configured to modulate the signal provided to the resonator 50 with information and thereby act as a source transmission modulator. The information used to modulate the signal provided to the resonator 50 can be provided to the compensation network 46A by the controller 42. The information can include control data that goes to the controller 22 of the transmitter module 20 via the transmitter resonator 30. In some embodiments, when the receiver module 40 is in the transmitter mode and the rectifier 46D is configured as an amplifier, the amplifier 46D can act as a modulator for the receiver module 40. The modulation employed can be any of amplitude modulation, frequency modulation, phase modulation, and combinations thereof. The information can be modulated onto the signal provided to the transmitter resonator 50 in digital form or in analog form. The information can be modulated onto the resonant frequency of the power signal provided to the transmitter resonator 50 by the source transmission modulator. In other embodiments, the information can be modulated onto a frequency different from the frequency of the power transmission. In other embodiments, the information may be modulated onto a harmonic of the resonant frequency of the power signal provided to the transmitter resonator 50. In still further embodiments, the resonant frequency of the power signal provided to the transmitter resonator 50 may be a harmonic of the frequency of the signal onto which the information is modulated. For example, and without limitation, the information transmitted in the manner described herein may include: the presence of the load 70, the charge level of the load 70, the power transfer efficiency, the charging rate of the load 70, the status of the load 70, the current voltage, the charge capacity, and the remaining time to charge the load 70.

[0288] Having described above how both the transmitter module 20 and the receiver module 40 can be reconfigured between operating in a transmitter mode and operating in a receiver mode, and having described how the signals from both the transmitter module 20 and the receiver module 40 can be modulated, it is apparent that Figure 1The system 10 may function as a full-duplex transmit-receive system for transmitting information in both directions via the resonators 30 and 50 . Figure 1 The system 10 may include Figure 1 and 7 The configuration described above allows information to be transmitted between the secondary sides when additional secondary sides are present.

[0289] In some embodiments, the primary side 12 and the secondary side 14 may communicate via Bluetooth (e.g., 2.4 GHz) or a signal frequency similar to that of GPS (e.g., 10 GHz). In some embodiments, there may be additional units that may separately collect data and transfer data back and forth between the primary side 12 and / or the secondary side 14. In some embodiments, WiFi may be employed to upload data from the primary side 12 and / or the secondary side 14 to an online portal (e.g., a website or mobile application associated with the primary side 12 and / or the secondary side 14).

[0290] In certain embodiments, it may be desirable to transfer power between two receiver modules 40 (e.g., peer-to-peer power transfer). For example, if a first electric bicycle with a first receiver is dead or low on power and a second electric bicycle with a second receiver and an at least partially charged battery is nearby, it may be desirable to transfer power from the second electric bicycle to the first electric bicycle. Such a situation may involve when, for example, there is no transmitter nearby. The facility of reconfiguring at least one of the two receiver modules 40 involved as a transmitter module enables this peer-to-peer power transfer. In general, this makes it possible to forward power between multiple secondary sides 14.

[0291] In other embodiments, it may be necessary to move in the reverse direction (i.e., from Figure 1 , Figure 6 and Figure 7 The ability of both the transmitter module 20 and the receiver module 40 to reconfigure between operating in transmitter mode and in receiver mode allows such power transfer in the "reverse" direction from the receiver module 40 to the transmitter module 20. The system thus allows for bidirectional power transfer. Given Figure 8 Device 26B and Fig. 9The fact that the devices 46D can be reconfigured to function as an amplifier or a rectifier, respectively, may collectively refer to such devices as "differential self-synchronous RF power amplifier / rectifiers". In view of the bidirectional nature of the power transmission, both the transmitter resonator 30 and the receiver resonator 50 may be described as "transmitter-receiver resonators" and both the transmitter module 20 and the receiver module 40 may be referred to as "power transmitter-receiver modules". Such configurations are useful in electric vehicles where kinetic energy is converted during braking and needs to be transferred to the battery. For example, without limitation, other systems, conditions, and arrangements where such altered direction of power transmission is applicable include several cell phones that may have different levels of remaining battery charge, and such an arrangement may be used to at least partially recharge another cell phone. More generally, when neither the transmitting system nor the receiving system has a permanent energy source (such as a power grid), then the bidirectional functionality may be employed to transfer energy in either direction.

[0292] In About Fig.31 In another embodiment described, a near-field radio frequency method

[2200] for transmitting power via a power signal at a power signal frequency is provided, the method comprising: providing

[2210] a dual-peak resonant near-field radio frequency power transfer system comprising a plurality of power transmit-receive modules, wherein each of the plurality of power transmit-receive modules is in wired communication with a transmitter-receiver resonator configured to exchange power with at least another transmit-receive module of the plurality of power transmit-receive modules; and operating the power transfer system according to an adjustable transfer mode ratio

[2220] for simultaneous capacitive power transfer and inductive power transfer.

[0293] Providing

[2210] a power transmission system may include providing a first power transmission-receiving module having a power signal tuner module among multiple power transmission-receiving modules, and operating

[2220] the power transmission system may include changing the transmission mode ratio by adjusting the power signal tuner module.

[0294] Providing

[2210] a power transmission system may include providing at least one power transmission-receiving module in wired communication with an associated transmitter-receiver resonator and having a modulator among a plurality of power transmission-receiving modules, and operating

[2220] the power transmission system may include: exchanging radio frequency signals between the associated transmitter-receiver resonator and a transmitter-receiver resonator in wired communication with at least another power transmission-receiving module among the plurality of power transmission-receiving modules; and modulating information onto the exchanged radio frequency signals. When a power load is present at the output end of one of the plurality of power transmission-receiving modules, for example, without limitation, the information modulated on the exchanged signal may include: one or more of: the presence of the power load, the charging level of the power load, the power transmission efficiency, the charging rate of the power load, the state of the power load, the presence of a voltage on the power load, the charge capacity of the power load, and the remaining time to charge the power load.

[0295] The information may be modulated onto the exchanged radio frequency signal by amplitude modulation, frequency modulation or phase modulation. The information may be modulated onto the exchanged radio frequency signal including modulating digital information or analog information onto the exchanged radio frequency signal.

[0296] Modulating the information onto the exchanged radio frequency signal may include modulating the information onto the power signal. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having a frequency different from the power signal frequency. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having a frequency that is a harmonic of the power signal frequency. Modulating the information onto the exchanged radio frequency signal may include modulating the information onto a signal having the power signal frequency as a harmonic.

[0297] Modulating information onto the exchanged radio frequency signals may include modulating a reflective property of an associated wire-connected transmitter-receiver resonator according to the information to impose the information on a signal reflected by the wire-connected transmitter-receiver resonator. Modulating information onto the exchanged radio frequency signals may include modulating a signal provided to the associated transmitter-receiver resonator according to the information.

[0298] The method

[2200] may include operating a power signal tuner module of a first power transmit-receive module of a plurality of power transmit-receive modules to modulate information onto an exchanged radio frequency signal. Each of the provided power transmit-receive modules may include a compensation network, and the compensation network may include a modulator, thereby allowing the compensation network to be operated to modulate information onto the exchanged radio frequency signal. At least one of the power transmit-receive modules may include a radio frequency oscillator that provides a signal to the at least one power transmit-receive module at a power signal frequency, and the radio frequency oscillator may include a modulator, thereby allowing information to be modulated in the oscillator onto the exchanged radio frequency signal.

[0299] Each of the provided plurality of power transmit-receive modules may be reconfigurable between a power transmitter mode and a power receiver mode; and the method may further include reconfiguring at least two of the plurality of power transmit-receive modules between the power transmitter mode and the power receiver mode to reverse the power transmission direction between the at least two transmit-receive modules. Each of the provided power transmit-receive modules may include a differential self-synchronous RF power amplifier / rectifier, which is capable of reconfiguring between an amplifier state and a rectifier state corresponding to the power transmitter mode and the power receiver mode of the power transmit-receive module, respectively; and the method may include reconfiguring the differential self-synchronous RF power amplifier / rectifier of the at least two transmit-receive modules between the amplifier state and the rectifier state. Each differential self-synchronous RF power amplifier / rectifier may include a phase shifter, which is adjustable, for reconfiguring the differential self-synchronous RF power amplifier / rectifier between the amplifier state and the rectifier state; and the method may include adjusting the phase shifter of each of the differential self-synchronous RF power amplifier / rectifiers in the at least two transmit-receive modules.

[0300] The WPT system 10 including the transmitter and / or receiver described herein can be integrated into various applications, such as but not limited to electric vehicles, electric boats, electric airplanes, electric trucks, electric bicycles, electric motorcycles, electric skateboards, etc. An exemplary non-limiting application is a shared bicycle fleet, in which various portable computers are provided that integrate one or more transmitters (e.g., primary side 12), and electric bicycles including receivers (e.g., secondary side 14) and batteries (as load 70) can be charged at the portable computers.

[0301] In certain applications, the primary side 12 or the secondary side 14 can be configured to transfer power using other systems not described herein, and the transfer mode can be adjusted from CPT to IPT to provide compatibility with other CPT systems and / or IPT systems even if the other systems are not specifically designed to work with the power transfer system described herein.

[0302] Although several exemplary schemes and embodiments have been discussed above, those skilled in the art will recognize certain modifications, permutations, additions and sub-combinations thereof. It is therefore intended that the following appended claims and the claims hereafter introduced be interpreted as including all such modifications, permutations, additions and sub-combinations consistent with the broadest interpretation of this specification as a whole.

[0303] In the first embodiment, the Figures 1 to 10 Each of the systems depicted in the figure forms a dual-peak near-field resonant wireless power transfer system 10, which is configured to simultaneously perform capacitive power transfer and inductive power transfer according to an adjustable transfer mode ratio at a variable resonant power signal oscillation frequency, and the system 10 includes: a transmitter subsystem 12, which includes a transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 and a power signal tuner module 26F, the tuner module 26F is configured to a power signal provided by the tuner module 26F to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 to adjust the transmit mode ratio; and a receiver subsystem 14, which includes a receiver antenna subsystem 52, 152, 252, 352, 154, 254, 354, 356 configured to receive power from the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 according to the transmit mode ratio.

[0304] The tuner module 26F may be configured to adjust the power signal by adjusting the phase difference between the current and the voltage of the power signal provided to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336. The transmitter subsystem 12 may further include: a controller 22; and at least one sensor 24, wherein the controller 22 is configured to receive sensor information from the at least one sensor 24 and automatically provide a tuning instruction to the tuner module 26F based on the sensor information, and the tuner module 26F is configured to adjust the phase difference between the current and the voltage of the power signal provided to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 according to the tuning instruction.

[0305] The system 10 resonates at a resonant frequency that is freely variable within a predetermined frequency band based on the degree of coupling between the transmitter subsystem 12 and the receiver subsystem 14. For example, without limitation, the predetermined frequency band may be an officially designed and reserved Industrial, Scientific, and Medical (ISM) band or a user-specific frequency band. The quality factor (Q) of the system 10 may be reduced to a degree that allows the power signal oscillation frequency to vary within the opposite extremes of the predetermined frequency band. The reduced Q value allows the system 10 to adopt any of a number of different resonant frequencies within the predetermined frequency band during the power transfer procedure. The coupling between the transmitter subsystem 12 and the receiver subsystem 14 and the associated power absorption of the resonant receiver subsystem 14 ensure that less electromagnetic radiation is emitted into the far field when the system 10 is in operation. Reference Figures 1 to 10 The arrangement as described herein, together with the frequency pattern immediately preceding, makes system 10 a dual peak near field resonant wireless power transfer system. It should be noted that in wireless power transfer system 10, power is transferred from the primary subsystem to the secondary subsystem via capacitive coupling or inductive coupling or both, rather than via electromagnetic radiation to any substantial extent.

[0306] With reference to the aforementioned drawings and Fig.11 In another embodiment described in the flowchart in , there is provided a near-field wireless method

[1000] for transmitting power bimodally according to an adjustable transmission mode ratio at a variable resonant power signal oscillation frequency, the method comprising: providing

[1010] a transmitter subsystem 12 including a power signal tuner module 26F and a transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336 configured to resonate at the resonant power signal oscillation frequency; providing

[1020] a receiver subsystem 52, 152, 252, 352, 154, 254, 354, 356 configured to resonate at the resonant power signal oscillation frequency. System 14; provides

[1030] a power signal from tuner module 26F to transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336 at a power signal oscillation resonant frequency; adjusts

[1040] the transmission mode ratio by adjusting the power signal from tuner module 26F to transmitter antenna subsystems 32, 132, 232, 332, 134, 234, 334, 336; and receives

[1050] the transmitted power according to the transmission mode ratio via receiver antenna subsystems 52, 152, 252, 352, 154, 254, 354, 356 at the power signal oscillation resonant frequency in the receiver subsystem 14. Adjusting

[1040] the transmit mode ratio may include adjusting a phase difference between a current and a voltage of a power signal provided to the transmitter antenna subsystem 32, 132, 232, 332, 134, 234, 334, 336.

[0307] Providing

[1010] the transmitter subsystem 12 may further include providing a controller 22 and at least one sensor 24, and the phase difference between the current and the voltage may be adjusted by the tuner module 26F based on sensor information received by the controller 22 from the at least one sensor 24 via a command of the controller 22. The controller 22 may automatically issue a command of the controller 22 to the tuner module 26F when the controller 22 receives the sensor information; and the tuner module 26F may automatically execute the command from the controller 22 to change the phase difference.

[0308] The method

[1000] may further include allowing

[1060] the resonant power signal oscillation frequency to vary within a predetermined frequency band. The predetermined frequency band may be an industrial, scientific and medical (ISM) band. Providing

[1010] the transmitter subsystem may include providing a transmitter subsystem that is demodulated to an extent that allows the resonant power signal oscillation frequency to vary within opposite extremes of the predetermined frequency band.

[0309] In reference Fig.12 , 13A and 13B and refer to Figures 1 to 10 In another embodiment, a multi-transmitter dual-peak near-field resonant wireless power transfer system 10′ is configured for simultaneous capacitive power transfer and inductive power transfer at a variable resonant power signal oscillation frequency according to an adjustable transfer mode ratio. The system 10′ includes a multi-transmitter subsystem 12′, which includes a plurality of transmitter resonators 30A′ to 30I′ each driven by a corresponding dedicated transmitter module 20A′ to 20I′, wherein each transmitter resonator and corresponding transmitter module (e.g., 30E′ and 20E′, respectively) can be connected to the above referenced Figures 1 to 10 The explanations presented are consistent. Fig.12 is a schematic representation of an embodiment of the system 10' in which the transmitter resonators 30A' to 30I' are presented as nine resonators in a row but are not depicted in their formalized spatial positions. An embodiment of the spatial layout of the multi-transmitter subsystem 12' is shown in Fig.13A and 13B In the system 10′, the resonant receiver subsystem 14 may be connected to the resonant receiver subsystem 14 described above and provided by Figures 1 to 10 The resonant receiver system referenced is the same or substantially similar. Fig.12 In the embodiment shown in FIG. 1 , the resonant receiver subsystem 14 may be implemented in, for example and without limitation, a cell phone or a digital "tablet". For clarity, Fig.13A The resonant receiver subsystem 14 is shown in broken outline in FIG. In an embodiment, each operating transmitter resonator 30A′ to 30I′ and each corresponding transmitter module 20A′ to 20I′ may be the same as described above and in Figures 1 to 10The transmitter resonator 30 and transmitter module 20 shown in FIG. 1 function in the same or substantially similar manner. An embodiment of the spatial layout of the multiple transmitter subsystem 12′ is shown in FIG. Fig.13A and 13B middle. Fig. 13B is the multi-transmitter subsystem 12′ relative to its Fig.13A The orientation in the view is in the opposite orientation.

[0310] exist Fig.12 , 13A In the exemplary embodiment of the system 10′ shown in FIG. 13B , the multi-transmitter subsystem 12′ includes nine pairs of transmitter resonators 30A′ to 30I′ and corresponding transmitter modules 20A′ to 20I′ arranged in a square array. The transmitter modules 20A′ to 20I′ are arranged in a square array. Fig.13A is shielded by the grounded substrate 35′ but can be Fig. 13B . In more general embodiments, other numbers of pairs of resonators and transmitter modules may be employed, and the resonator array need not be square or rectangular. By way of example and not limitation, the resonator array may have a hexagonal arrangement. In certain embodiments, it is preferred to pack the array tightly within the constraints of a grounded shielding mesh that separates and defines the transmitter resonators 30A′ to 30I′. The grounded shielding mesh 33′ laterally confines the array of transmitter resonators 30A′ to 30I′. The grounded shielding mesh 33′ is disposed at a consistent distance 37′ from the perimeter of each of the transmitter resonators 30A′ to 30I′ to ensure consistent electric field behavior and associated capacitance between the transmitter resonators 30A′ to 30I′ and the grounded shielding mesh 33′. The term “shielding distance” is used herein to describe this distance between the transmitter resonators 30A′ to 30I′ and the grounded shielding mesh 33′.

[0311] In one embodiment, the ground shield mesh 33' ensures that the electric fields of the transmitter resonators 30A' to 30I' will be completely spatially decoupled and thus spatially independent. The transmitter resonators 30A' to 30I' may have magnetic fields that are selected to be decoupled from each other by virtue of spatial positioning. In other embodiments, the ground shield mesh 33' may be formed of or coated with a highly conductive ferrite material in order to decouple the magnetic fields generated by the transmitter resonators 30A' to 30I'.

[0312] like Fig.13A and 13BAs shown in FIG. 1 , the transmitter resonators 30A′ to 30I′ and their corresponding transmitter modules 20A′ to 20I′ can be mounted substantially in a row on opposite sides of a ground substrate 35′, wherein each transmitter resonator (e.g., 30E′) is proximate to its corresponding transmitter module (20E′). In other embodiments, there may not be a fixed spatial relationship between the transmitter resonators and their corresponding transmitter modules. The array of transmitter resonators 30A′ to 30I′ shares a common structure composed of Fig.13A The collective upper surface of the transmitter resonators 30A′ to 30I′ in the array defines a common emitting surface. For aesthetic and protective reasons, the array of transmitter resonators 30A′ to 30I′ may be covered with a dielectric plate. Fig.13A A dielectric plate separates the receiver subsystem 14 from the transmitter resonators 30A' to 30I'.

[0313] exist Fig.12 and 13A , an embodiment of the resonant receiver subsystem 14 is schematically shown as overlapping a subset of the plurality of transmitter resonators 30A′ to 30I′. Fig.12 and 13A , overlapping transmitter resonators are shown as 30D', 30E', ​​30G' and 30H'. Fig.13A , the resonant receiver subsystem 14 is shown as a dotted rectangle on mutually adjacent transmitter resonators 30D′, 30E′, 30G′, and 30H′. The controller of any of the transmitter modules 20A′ to 20I′ can determine the presence or absence of a resonant receiver subsystem 14 that is close to or overlaps its corresponding transmitter resonator 30A′ to 30I′, and based on such detection, the controller can turn on or off the power signal to its corresponding transmitter resonator 30A′ to 30I′.

[0314] If the power amplifiers of the transmitter modules 20A′ to 20I′ supply power signals to the transmitter resonators 30A′ to 30I′ so that the transmitter resonators 30A′ to 30I′ transmit power, and the controllers of the transmitter modules 20A′, 20B′, 20C′, 20F′ and 20I′ determine that there are no resonant receivers close to the transmitter resonators 30A′, 30B′, 30C′, 30F′ and 30I′ within their frequency ranges, then their controllers may shut off the power signals to the transmitter resonators 30A′, 30B′, 30C′, 30F′ and 30I′.

[0315] If the power amplifiers of the transmitter modules 20A′ to 20I′ do not supply power signals to the transmitter resonators 30A′ to 30I′, the controllers for the transmitter resonators 30D′, 30E′, 30G′, and 30H′ can determine the presence of the resonant receiver subsystem 14 that overlaps with the resonators 30D′, 30E′, 30G′, and 30H′ and is close to the resonators 30D′, 30E′, 30G′, and 30H′, and turn on the transmittable power provided by the transmitter modules 20D′, 20E′, 20G′, and 20H′ to the transmitter resonators 30D′, 30E′, 30G′, and 30H′. This configuration ensures that only the transmitter resonators close to the resonant receiver subsystem 14 are drawing power and transmitting power to the resonant receiver subsystem 14.

[0316] The input impedance of the transmitter resonators 30A′ to 30I′ can be used to detect the presence or absence of a resonant receiver subsystem 14 in proximity to the transmitter resonator. The transmitter resonator input impedance varies with the presence or absence of a resonant receiver subsystem 14 in proximity to the transmitter resonator. As described above, reference Figure 6 , the effect of a particular resonant receiver subsystem 14 is different so as to allow detection of not only the presence and absence of a receiver, but also detection of characteristics such that the type of receiver can be identified by its effect on the transmitter resonator input impedance. In certain embodiments, the size of the receiver resonator has a significant effect on the input impedance of the transmitter resonators 30A′ to 30I′.

[0317] In an embodiment of the system 10', as in Fig.12 and 13B The transmitter module 20E' shown in FIG. 1 is a transmitter module associated with one of the four transmitter resonators 30D', 30E', ​​30G', and 30H' overlapped by the resonant receiver subsystem 14. Figure 6 and Figure 8 The detailed structure of each of the transmitter modules 20A' to 20I' is provided in . The flow is started without the power amplifier 26B of the transmitter module 20A' to 20I' providing a power signal to the corresponding transmitter resonator 30A' to 30I'.

[0318] Now focusing on the transmitter module 20E′, in this embodiment, its load detector 24A is configured to measure the input impedance of the transmitter resonator 30E′. The load detector 24A provides the input impedance measurement result to the controller 22. A preset input impedance measurement value is stored in a register in the controller 22, and the preset input impedance measurement value represents the input impedance of the transmitter resonator 30E′ in the absence of any resonant receiver subsystem close to the transmitter resonator 30E′. As shown in Fig.12As shown in , placing the resonant receiver subsystem 14 in proximity to the transmitter resonator 30E′ results in a new and different input impedance measurement being made by the load detector 24A, the results of which are supplied by the load detector 24A to the controller 22. The controller 22 compares the new input impedance measurement (referred to herein as the "first input transmitter resonator impedance change" or "main transmitter resonator input impedance change") to a preset impedance measurement value stored in a temporary register. Based on this first input impedance change, the controller 22 makes a determination as to whether a receiver resonator (e.g., a resonator of the resonant receiver subsystem 14) is in proximity to the transmitter resonator 30E′. In order to make a determination as to the presence or absence of a receiver resonator in proximity to the transmitter resonator 30E′, the controller 22 may be pre-programmed with a minimum input impedance change that must be exceeded before the controller 22 deems a receiver resonator to be present.

[0319] If the controller 22 determines that there is a receiver resonator (e.g., a resonator of the resonant receiver subsystem 14) proximate to the transmitter resonator 30E′, the controller 22 instructs the power amplifier to assume an “on” state. Power is thereby provided to the transmitter resonator 30E′ and, in turn, is transferred to the resonant receiver subsystem 14. If the controller 22 determines that there is no receiver resonator (e.g., a resonator of the resonant receiver subsystem 14) proximate to the transmitter resonator 30E′, the controller 22 instructs the power amplifier to assume an “off” state. Power is thereby not provided to the transmitter resonator 30E′ and, in turn, is not transferred to the resonant receiver subsystem 14. The same procedure is performed independently by each transmitter module 20A′ to 20I′ with respect to its corresponding transmitter resonator 30A′ to 30I′. Thus, the power amplifiers of the transmitter resonators 30D′, 30E′, 30G′, and 30H′ overlapped by the resonant receiver subsystem 14 are turned on and the power amplifiers of the transmitter resonators 30A′, 30B′, 30C′, 30F′, and 30I′ not overlapped by the resonant receiver subsystem 14 are turned off.

[0320] It should be noted that receiver resonators of different sizes present significantly different impedances at point 24E to the load detector 24A of the transmitter module 20. The impedance difference measured when a given receiver resonator partially overlaps a transmitter resonator compared to when it completely overlaps the transmitter resonator is not as significantly different as the impedance with different sizes of receiver resonators. This allows the controller 22 of any transmitter module 20A′ to 20I′ to distinguish between a small receiver resonator and a large receiver resonator that is close to the corresponding transmitter resonator 30A′ to 30I′.

[0321] According to one embodiment, setting the power signal frequency and phase between those transmitter resonators (e.g., 30D′, 30E′, 30G′, and 30H′) overlapped by a resonant receiver subsystem (e.g., resonant receiver subsystem 14) is described herein. In order to maximize the efficiency of transferring power from the combination of transmitter resonators 30D′, 30E′, 30G′, and 30H′ that are receiving power, the power signals in the transmitter resonators 30D′, 30E′, 30G′, and 30H′ need to have the same frequency and be in phase with each other. The frequency of the power signal in a given transmitter resonator 30D′, 30E′, 30G′, and 30H′ may be different within the allowed frequency band, as previously described above and with reference to Figures 1 to 10 As stated, Fig.12 , 13A The requirement in this current embodiment of 13B is for the frequencies of the power signals in the transmitter resonators 30D′, 30E′, 30G′ and 30H′ to be adjusted to be the same and then for their phases to be locked together so that the power signals from the transmitter resonators 30D′, 30E′, 30G′ and 30H′ will be completely synchronized and in phase.

[0322] In one embodiment, to ensure that the controllers 22 of the overlapping transmitter resonators 30D', 30E', ​​30G' and 30H' all set their corresponding oscillators 26A to the same frequency, the controllers 22 of the transmitter modules 20A' to 20I' are all provided with the same table of frequencies selected within any given allowed frequency band (e.g., an ISM band). Within the ISM band, a number of discrete frequencies are selected for inclusion in the frequency table. Thus, the number of listed frequencies within the ISM band is finite and limited, and the listed frequencies are spaced widely enough that the various controllers 22 of the transmitter modules 20D', 20E', 20G' and 20H' can determine the power signal frequency based on the first impedance difference described above. Despite the small changes in those impedances, all of the controllers 22 of the transmitter modules 20D', 20E', 20G' and 20H' select the same discrete frequency for the power signal of their corresponding oscillator 26A and power amplifier 26B from the allowed frequencies in the band.

[0323] In one embodiment, to ensure that the transmitter resonators 30D′, 30E′, 30G′, and 30H′ all have not only the same power signal frequency, but also the same phase, the following program steps are employed and programmed into the software of each controller 22 of the transmitter modules 20A′ to 20I′. Statistically, the first of the independent controllers 22 of the transmitter modules 20D′, 20E′, 20G′, and 20H′ will first turn on its corresponding oscillator 26A and power amplifier 26B to supply power to the resonant receiver subsystem 14 via its transmitter resonator. The second independent controllers of the other independent controllers 22 of the independent controllers 22 of the transmitter modules 20D′, 20E′, 20G′, and 20H′ will measure the input impedance of their corresponding transmitter resonators and detect the small secondary changes in impedance caused by the first transmitter resonator acting through their corresponding load detectors 24A. In effect, the second controller 22 experiences a reflection of the impedance of the first transmitter resonator through the interaction of the first transmitter resonator with the resonant receiver subsystem 14. The second controller 22 is programmed to conclude that, based on the secondary impedance change, the other controller has first turned on its oscillator 26A and power amplifier 26B. After making this inference, the second controller 22 then turns on its oscillator 26A and power amplifier 26B and varies the phase of its power signal while measuring the power transmitted by its corresponding transmitter resonator using its transmitter power sensor 24B. The second controller 22 then varies the phase of its oscillator and searches for the phase at which maximum power transfer occurs and sets the phase of the oscillator to that value. The oscillator phase determined in this manner will ensure that the phase of the power signal transmitted by the second transmitter resonator is equal to the phase of the power signal transmitted by the first transmitter resonator to the resonant receiver subsystem 14. In an embodiment, the setting of the oscillator phase is based on substantially maximizing power transfer, rather than making the power signal phases absolutely equal.

[0324] In another embodiment, again based on the transmitter resonators 30D′, 30E′, 30G′, and 30H′ being overlapped by the resonant receiver subsystem 14, the detection of the proximity of the resonant receiver subsystem 14 is based on the test signal power drawn by the transmitter resonators 30D′, 30E′, 30G′, and 30H′. In this embodiment, a low amplitude power signal is initially maintained by the oscillators and power amplifiers corresponding to all of the transmitter resonators 30A′ to 30I′. The controllers 22 of all of the transmitter modules 20A′ to 20I′ then sense the power drawn by their corresponding transmitter resonators 30 using their corresponding transmitter power sensors 24B. Using their corresponding transmitter power sensors 24B, the controllers 22 of the transmitter modules 20D′, 20E′, 20G′, and 20H′ sense that power is being drawn by their corresponding transmitter resonators 30D′, 30E′, 30G′, and 30H′. Based on the detection of the drawn test signal power, the controller 22 of the transmitter modules 20D', 20E', 20G' and 20H' turns on the full power of their corresponding power amplifiers 26B. The term "first test signal power draw" is used herein to describe the power drawn from the test signal via the transmitter resonators 30D', 30E', ​​30G' and 30H'. After a suitable test period, the test power signals of the power amplifiers 26B of the transmitter resonators 30A', 30B', 30C', 30F' and 30I' that are not overlapped by the resonant receiver subsystem 14 can be turned off.

[0325] Equivalent to the impedance-based embodiment described above, the controller 22 of the transmitter modules 20D', 20E', 20G', and 20H' may require a threshold power draw in order to consider a resonant receiver subsystem 14 to be present proximate to its corresponding transmitter resonator 30D', 30E', ​​30G', and 30H'.

[0326] In one embodiment, to ensure that the controllers 22 of the overlapping transmitter resonators 30D', 30E', ​​30G' and 30H' all set their corresponding oscillators 26A to the same frequency, the controllers 22 of the transmitter modules 20A' to 20I' are all provided with the same table of frequencies selected within any given allowed frequency band (e.g., an ISM band). Within the ISM band, a number of discrete frequencies are selected for inclusion in the frequency table. Thus, the number of listed frequencies within the ISM band is finite and limited, and the listed frequencies are spaced widely enough that the various controllers 22 of the transmitter modules 20D', 20E', 20G' and 20H' can determine the power signal frequency based on the first test signal power draw described above. Despite the small variation in those power draw values, all of the controllers 22 of the transmitter modules 20D', 20E', 20G' and 20H' select the same discrete frequency for the power signal of their corresponding oscillator 26A and power amplifier 26B from among the allowed frequencies in the band.

[0327] In one embodiment, to ensure that the transmitter resonators 30D′, 30E′, 30G′, and 30H′ all have not only the same power signal frequency, but also the same phase, the following program steps are employed and programmed into the software of each controller 22 of the transmitter modules 20A′ to 20I′. Statistically, the first of the independent controllers 22 of the transmitter modules 20D′, 20E′, 20G′, and 20H′ will first turn on its corresponding oscillator 26A and power amplifier 26B to supply power to the resonant receiver subsystem 14 via its transmitter resonator. The second independent controllers of the other independent controllers 22 of the independent controllers 22 of the transmitter modules 20D′, 20E′, 20G′, and 20H′ will measure the power draw of their corresponding transmitter resonators and detect small secondary changes in the power draw due to the first transmitter resonator functioning through their corresponding transmitter power sensors 24B. In effect, the second controller 22 experiences reflections of the impedance of the first transmitter resonator via the interaction of the first transmitter resonator with the resonant receiver subsystem 14. The second controller 22 is programmed to conclude that the other controller has first turned on its oscillator 26A and power amplifier 26B based on the secondary power draw variation. After making this inference, the second controller 22 then turns on its oscillator 26A and power amplifier 26B and varies the phase of its power signal while measuring the power transmitted by its corresponding transmitter resonator using its transmitter power sensor 24B. The second controller 22 then searches for the phase at which maximum power transfer occurs and sets the oscillator to that phase. The oscillator phase set in this manner ensures that the phase of the power signal transmitted by the second transmitter resonator to the resonant receiver subsystem 14 is equal to the phase of the power signal transmitted by the first transmitter resonator to the resonant receiver subsystem 14. In an embodiment, the setting of the oscillator phase is based on substantially maximizing power transfer, rather than absolutely equalizing the power signal phases.

[0328] In one embodiment, when two different resonating receiver subsystems are proximate to the multiple transmitter subsystem 12′ and overlap with different transmitter resonators or combinations thereof in the transmitter resonators 30A′ to 30I′, there is no a priori reason why the two different transmitter resonators or two different groups of transmitter resonators overlapped by the two resonating receiver systems should operate at the same frequency or phase, nor is there a requirement for them to do so. The grounded shielding mesh 33′ ensures this multi-path independence by decoupling all of the individual transmitter resonators 30A′ to 30I′ from one another. However, the transmitter resonators overlapped by a particular resonating receiver subsystem need to have their corresponding power signal amplifiers actively synchronized by their controllers, as described above. This can result in two different transmitter resonators or two different groups of resonators operating at two specific different locking frequencies in a frequency band, with all signals in a particular group being in phase with one another.

[0329] In the foregoing, it has been described how two transmitter resonators transferring power to the same receiver resonator can be programmed to operate so as to ensure that the two transmitter resonators carry power signals that are in phase, thereby ensuring maximum power transfer. Fig.14 14B') are transmitting to two substantially similar corresponding receiver subsystems 14A and 14B. A different situation occurs. Both transmitter resonators 30A' and 30B' have fringing fields with field lines extending from, for example, transmitter resonator 30A' to receiver subsystem 14B' and from transmitter resonator 30B' to receiver subsystem 14A. Generally, there are no specific physical structures in system 10' to prevent fields of, for example, transmitter resonator 30A' from interacting with receiver resonators of receiver subsystem 14B.

[0330] In one embodiment, when both transmitter resonators 30A′ and 30B′ serve the same large receiver resonator that overlaps both transmitter resonators 30A′ and 30B′ (eg, Fig.13A ), the fringing fields are not inherently a problem because the two transmitter resonators 30A′ and 30B′ will be running the same frequency power signal with the same phase. Fig.14 In the case shown in , the requirement is to ensure that any fringe fields of a given transmitter resonator (e.g., 30A′) that interacts with a receiver subsystem (e.g., 14B that is intended to receive power from an adjacent transmitter resonator 30B′) do not allow power to be parasitic from the transmitter resonator 30A′. One method of achieving this goal is to drive two adjacent transmitter resonators 30A′ and 30B′ 180° out of phase with each other so that the overlapping fringe fields from the transmitter resonators 30A′ and 30B′ will largely cancel each other.

[0331] Since either transmitter resonator 30A′ and 30B′ treats the other transmitter resonator 30A′ and 30B′ as a parasitic when the power signals of the transmitter resonators are not 180° out of phase, the controller 22 of each of the transmitter resonators 30A′ and 30B′ can increment the phase of the signal from each corresponding oscillator while measuring the power transmitted by the corresponding transmitter resonator 30A′, 30B′ using the corresponding transmitter power sensor 24B. The controller 22 can then search for the adjusted oscillator phase that provides the maximum transmitted power via the corresponding transmitter resonator 30A′, 30B′ and then set the phase of the oscillator to the corresponding phase.

[0332] The frequency and phase arrangement of each resonant receiver system, whether similar or different in size, as described above, ensures that both resonant receiver systems receive maximum transferred power. In a general embodiment, there may be a large number of transmitter resonators and several different resonant receiver subsystems may be receiving power, each resonant receiver subsystem receiving power from its own corresponding individual group of transmitter resonators at a frequency and phase selected by a controller corresponding to the transmitter resonator in the group. As a result of maximizing power transfer to each of the adjacent transmitter resonators, adjacent transmitter resonators transmitting power to different receiver subsystems may operate 180° out of phase. The process of maximizing power transfer adjusts the oscillator phase. Because the impedances of the various transmitter modules are complex and have slight variations in resistance, inductance, and capacitance, the phase angles of the different oscillators at the point of maximum power transfer may not be exactly equal (or exactly 180° different) when the power signals in the transmitter resonators are actually equal (or exactly 180° different).

[0333] To the extent that system 10' includes a circuit having an air gap between the primary side and the secondary side, in the transmitter resonator (e.g., Figure 6 Any power transfer measured or maximized based on the measurement results of the transmitter power sensor 24B can also be measured in the secondary circuit (e.g., at point 24E in FIG. 24B ). Figure 7 44C in FIG. 4 ), based on the measurement by the receiver power sensor 44A. The measurement may be provided by the transmitter power sensor 24B to the controller 42 of the receiver module 40, which in turn may communicate the measurement to the controller 22 of the transmitter module 20 by one of the means described above.

[0334] The concept of a multi-transmitter near-field resonant wireless power transfer system has been explained above with reference to system 10′, which is configured for simultaneous capacitive power transfer and inductive power transfer according to an adjustable transfer mode ratio at a variable resonant power signal oscillation frequency. In more general embodiments, the multi-transmitter near-field resonant wireless power transfer system need not be specifically a bimodal system and may be a purely capacitive or purely inductive power transfer system.

[0335] In another embodiment, Fig.15As shown in the flowchart of , a wireless near-field method

[1100] for transmitting power from a multiple transmitter subsystem 12′ to a single resonant receiver subsystem 14 at a variable resonant power signal oscillation frequency includes: providing

[1110] a multiple transmitter subsystem 12′ including a plurality of mutually independent transmitter resonators 30A′ to 30I′, each of the transmitter resonators being driven by a corresponding transmitter module 20A′ to 20I′, each transmitter module 20A′ to 20I′ being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and all transmitter resonators 30A′ to 30I′ having a common transmitting surface; arranging

[1120] a resonant receiver subsystem 14 proximate to the common transmitting surface, the resonant receiver subsystem including a plurality of mutually independent transmitter resonators ( Fig.13A a single receiver resonator 50 overlapping two or more of the plurality of mutually independent transmitter resonators 30A′ to 30I′; measuring

[1130] the input impedance of each of the transmitter resonators 30A′ to 30I′; and setting

[1140] the power signal to each of the plurality of mutually independent transmitter resonators 30A′ to 30I′ to one of an off state and an active state based on the corresponding measured resonator input impedance.

[0336] The method

[1100] may further include: Fig.13A The input impedance measured for each of the transmitter resonators 30D′, 30E′, 30G′ and 30H in the embodiment is selected from the plurality of preset power signal oscillation frequencies for the corresponding transmitter resonator ( Fig.13A 30D′, 30E′, 30G′ and 30H′) in select the power signal oscillation frequency

[1150] .

[0337] The method

[1100] may further include placing each active transmitter resonator ( Fig.13A The power signal settings

[1160] of 30D′, 30E′, 30G′ and 30H′) are the corresponding selected frequencies.

[0338] The method

[1100] may further include applying to each corresponding transmitter resonator ( Fig.13A The phase adjustment

[1170] of the power signal of the transmitter resonator ( 30D′, 30E′, 30G′ and 30H) is performed by the transmitter resonator ( Fig.13A The power transmission of 30D′, 30E′, 30G′ and 30H′) is basically the largest phase.

[0339] In another embodiment, Fig.16As shown in the flowchart of , a wireless near-field method

[1200] for transmitting power from a multiple transmitter subsystem 12′ to a single resonant receiver subsystem 14 at a variable resonant power signal oscillation frequency includes: providing

[1210] a multiple transmitter subsystem 12′ including a plurality of mutually independent transmitter resonators 30A′ to 30I′, each of the transmitter resonators being driven by a corresponding transmitter module 20A′ to 20I′, each transmitter module 20A′ to 20I′ being independently settable to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and all transmitter resonators 30A′ to 30I′ having a common transmitting surface; arranging

[1220] a resonant receiver subsystem 14 close to the common transmitting surface, the resonant receiver subsystem including a plurality of mutually independent transmitter resonators ( Fig.13A a single receiver resonator 50 overlapping two or more of the plurality of mutually independent transmitter resonators 30A′ to 30I′); measuring

[1230] the power drawn by each of the transmitter resonators 30A′ to 30I′ from a test signal; and setting

[1240] the power signal to each of the plurality of mutually independent transmitter resonators 30A′ to 30I′ to one of an off state and an active state based on the corresponding measured resonator test power draw.

[0340] The method

[1200] may further include providing a method based on an active transmitter resonator ( Fig.13A The measured test power drawn by each of the transmitter resonators 30D′, 30E′, 30G′ and 30H in the transmitter resonator 30D′, 30E′, 30G′ and 30H) is selected from the plurality of preset power signal oscillation frequencies for the corresponding transmitter resonator ( Fig.13A 30D′, 30E′, 30G′ and 30H) in select

[1250] the power signal oscillation frequency.

[0341] The method

[1200] may further include placing each active transmitter resonator ( Fig.13A The power signal settings

[1260] of 30D′, 30E′, 30G′ and 30H) are the corresponding selected frequencies.

[0342] The method

[1200] may further include applying to each corresponding transmitter resonator ( Fig.13A The phase adjustment

[1270] of the power signal of the transmitter resonator ( 30D′, 30E′, 30G′ and 30H) is performed by the transmitter resonator ( Fig.13A The power transmission of 30D′, 30E′, 30G′ and 30H) is basically the largest phase.

[0343] In another embodiment, Fig.17As shown in the flow chart of FIG. 1 , power is transmitted from a multi-transmitter subsystem 12′ to two or more receiver subsystems 14A, 14B (at a variable resonant power signal oscillation frequency) Fig.14 The wireless near-field method

[1300] of claim 1300 comprises: providing

[1310] a plurality of mutually independent transmitter resonators 30A′ to 30I′ (in Fig.14 ) of the multi-transmitter subsystem 12 ′, each of the transmitter resonators is composed of a corresponding transmitter module 20A′ to 20I′ (see Fig. 13B ) driven, each transmitter module 20A′ to 20I′ can be independently set to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and all transmitter resonators 30A′ to 30I′ have a common transmitting surface; two or more resonant receiver subsystems 14A, 14B are arranged

[1320] close to the common transmitting surface, each resonant receiver subsystem includes a transmitter resonator ( Fig.14

[1330] a single receiver resonator overlapping one or more of the transmitter resonators 30A′, 30B′ in the transmitter resonator; measuring

[1330] the input impedance of each of the transmitter resonators 30A′, 30B′; and setting

[1340] the power signal to each of the plurality of mutually independent transmitter resonators 30A′ to 30I′ to one of an off state and an active state based on the corresponding measured resonator input impedance.

[0344] The method

[1300] may further include based on an active transmitter resonator ( Fig.14 The input impedance measured for each of the transmitter resonators 30A′, 30B′ in the transmitter resonator 30A′, 30B′ is used to select a power signal oscillation frequency for the corresponding transmitter resonator 30A′, 30B′ from among the plurality of preset power signal oscillation frequencies

[1350] .

[0345] The method

[1300] may further include setting

[1360] the power signal of each active transmitter resonator 30A', 30B' to a corresponding selected frequency.

[0346] The method

[1300] may further include adjusting

[1370] the phase of the power signal applied to each corresponding transmitter resonator 30A', 30B' to be phased by the transmitter resonator 30A', 30B' (at Fig.14 The power transfer in the middle phase is basically the largest.

[0347] In another embodiment, Fig.18 As shown in the flow chart of FIG. 1 , power is transmitted from a multi-transmitter subsystem 12′ to two or more receiver subsystems 14A, 14B (at a variable resonant power signal oscillation frequency) Fig.14The wireless near-field method

[1400] of claim 1400 comprises: providing

[1410] a plurality of mutually independent transmitter resonators 30A′ to 30I′ (in Fig.14 ) of the multi-transmitter subsystem 12 ′, each of the transmitter resonators is composed of a corresponding transmitter module 20A′ to 20I′ (see Fig. 13B ) driven, each transmitter module 20A′ to 20I′ being independently set to one of a plurality of preset power signal oscillation frequencies in a preset frequency band, and all transmitter resonators 30A′ to 30I′ having a common transmitting surface; two or more resonant receiver subsystems 14A, 14B being arranged

[1420] close to the common transmitting surface, each resonant receiver subsystem comprising a single receiver resonator overlapping one or more of the transmitter resonators (transmitter resonators 30A′, 30B′ in FIG. 13 ); measuring

[1430] the power drawn by each of the transmitter resonators 30A′ to 30I′ from a test signal; and setting

[1440] the power signal to each of the plurality of mutually independent transmitter resonators 30A′ to 30I′ to one of an off state and an active state based on the corresponding measured resonator test power draw.

[0348] The method

[1400] may further include based on an active transmitter resonator ( Fig.14 The input impedance measured for each of the transmitter resonators 30A′, 30B′ in the transmitter resonator 30A′, 30B′ is used to select a power signal oscillation frequency for the corresponding transmitter resonator 30A′, 30B′ from among the plurality of preset power signal oscillation frequencies

[1450] .

[0349] The method

[1400] may further include setting

[1460] the power signal of each active transmitter resonator 30A', 30B' to a corresponding selected frequency.

[0350] The method

[1400] may further include adjusting

[1470] the phase of the power signal applied to each corresponding transmitter resonator 30A', 30B' to be phased by the transmitter resonator 30A', 30B' (at Fig.14 The power transfer in the middle phase is basically the largest.

[0351] In reference Fig. 20A and 20B , Fig.21A and 21B ,as well as Fig.22A and 22B Based on Figures 1 to 10 and Figure 12 to Figure 14 In another embodiment of the system, according to Fig.19AThe schematic diagram of FIG. 1 presents a near-field resonant wireless power transfer system 10 ″ for wirelessly transferring power from a photovoltaic solar cell 420 to an electrical load 70 ″. Fig.19A The marks on the Fig.13A and Fig. 13B The parallel relationship between Figure 6 and Figure 7 The parallel relationship is also clear at a glance. With this numbering scheme, DC power is supplied from the solar cell 420 to the transmitter module 20" via the power conditioning unit (PCU) 430. In addition to converting the DC voltage and DC current into levels that can be further transmitted by the power amplifier 26B", the PCU 430 also provides appropriately regulated voltage and current levels to drive the rest of the system components in the transmitter module 20", including small signal electronic components. The PCU 430 represents an adaptively changing load of the solar cell 420 in order to adapt to the varying power provided by the solar cell 420 and the varying output impedance presented by the solar cell 420 to the PCU 430. This allows the PCU 430 to absorb power from the solar cell 420 at the maximum possible rate at all times and temperatures, regardless of changes in the power from the solar cell 420.

[0352] The oscillator 26A" may be used to modulate the power amplifier 26B" at a frequency suitable for wireless power transfer as described above. The power amplifier 26B" may be connected to the Figure 8 , with the DC power being supplied from PCU 430 rather than as DC voltage source 127E. In an alternative embodiment, power amplifier 26B" may be suitably provided with circuitry for sustaining oscillation itself, as is well known in the art of radio systems, thereby eliminating oscillator 26A".

[0353] Power may be delivered to the transmit resonator 30" via the transmit tuning network 28". Fig.19A The transmission tuning network is Figure 6 The transmitter resonator 30" may have a surface area having an extension that may be at least a major portion of the extension of the active solar radiation receiving surface of the solar cell 420. All of these components of the transmitter module 20" are under the control of the controller 22", as described above. Figure 6 The corresponding components of the transmitter module 20 are under the control of the controller 22. For the sake of clarity, Fig.19A All components of the transmitter module 20" are shown in FIG. Figure 6The sensors and detectors 24A, 24B, 24C and 24D may also be present in an equivalent form in the transmitter module 20" and connected to the controller 22", and may realize the same as those already mentioned. Figure 6 The same effect as described.

[0354] Power can be wirelessly transferred from the transmitter module 20" to the receiver module 40" via the transmitter resonator 30" and the receiver resonator 50". The power can then be transferred from the receiver module 40" to the DC load 70". Power can be transferred between the transmitter resonator 30" and the receiver resonator 50" by near-field wireless transfer, as described above with reference to Figures 6 to 10 According to Fig.19A The near-field wireless power transfer is not limited to bimodal and can be purely capacitive or purely inductive.

[0355] The receiver module 40" may have Figure 7 For clarity, the receiver module 40 has the same components. Fig.19A A reduced set of components is shown in . Figure 7 The sensor 44A and the detector 44B are not shown in equivalent form. Fig.19A But it can exist. Fig.19A The receiver tuning network 48″ in can be a combination of the compensation network 46A, the matching network 46B, the rectifier 46D and the filter 46C. The power can be transmitted from the receiver tuning network 48″ to the load manager 46E″, and both the receiver tuning network and the load manager can be under the control of the receiver controller 42″.

[0356] Just Figure 7 With respect to rectifier 46D, shown in greater detail in FIG. 4 , the input impedance of this device is directly dependent on the load seen by the output of the device.

[0357] In operation, the near-field resonant wireless power transfer system 10" can be used with Figure 1 and Figures 6 to 10 The near-field resonant wireless power transfer system 10 functions in the same manner as the near-field resonant wireless power transfer system 10, with the difference being that the voltage VDD applied to each power amplifier 26B" is replaced by a power signal from a power conditioning unit (PCU) 430, which in turn receives its power from an associated power source (in the embodiment, a solar cell 420).

[0358] In another embodiment, the Fig.19A The system shown in omits the power conditioning unit 430, and instead the power delivery system 10" is configured or operated to also function as a power conditioning system. This can be achieved by configuring the controller 22" in software, for example without limitation, to operate based on the power conditioning unit 430. Figure 6The power level measured by the transmitter power sensor 24B adjusts the input DC equivalent resistance of the power amplifier 26B″. The term “input DC equivalent resistance” is used herein to describe the ratio of the DC voltage to the DC current at the DC terminals of the power amplifier 26B. Although the controller 22″ will make adjustments based on the power measurements, it is expected that the maximum power point of the transmitted power will be achieved when the input impedance of the power amplifier 26B″ matches the output impedance of the solar cell 420. In this embodiment, the system 10″ acts as a system known in the industry as a “maximum power point tracker” and ensures that power is always transmitted at a rate that is more suitable for the power consuming load than the rate that would be obtained if the power supply was not regulated. In another embodiment, the controller 22″ can be configured to measure the output impedance of the power source, which in this embodiment is the solar cell 420, and then adjust the input impedance of the power amplifier 26B″ based on the measured output impedance of the solar cell 420.

[0359] In addition to adjusting the input impedance of the power amplifier 26B", the controller 22" may also adjust one or more of the settings of the transmission tuning network 28" and the frequency of the oscillator 26A". In addition, the transmitter controller 22" may be based on Figure 6 The measurement results of the load detector 24A shown in FIG. 1 are adjusted as described above. Figure 6 More details are given about the circuitry of transmitter modules 20 and 20″. Load detector 24A is Figure 6 The effect of load 70" is sensed at point 24E.

[0360] The receiver controller 42" may also be based on the receiver power sensor 44A and the load detector 44B (both shown in FIG. Figure 7 The measurement results of (in) are used to adjust one or more of the settings of the receiver tuning network 48" and the load management system 46E" to improve the efficiency of power transmission.

[0361] When considering the power regulation functionality of system 10″, it can be appreciated that there is no a priori reason why the power transfer functionality of the system should be restricted to near-field wireless transmission across an air gap, such as in Fig.19A Therefore, in another embodiment, based on Fig.19A The components of the system 10″ are Fig.19B. The transmission tuning network 28" is in direct electrical communication with the receiver tuning network 48" via a suitable non-air gap connection 60". This communication is via an RF power signal and constitutes the power transmitted in and by the system. Suitable reactance electronic components can be employed in well-known configurations to decouple any DC voltage and current levels in the transmitter module 20" from such levels in the receiver module 40". The transmitter resonator 30" and the receiver resonator 50" are not present in this embodiment and are eliminated by the direct communication connection between the transmission tuning network 28" and the receiver tuning network 48".

[0362] Can be considered Fig.19B Better understanding Fig.19A and Fig.19B The power transfer system functions as a power conditioning system, wherein the transmitter resonator 30″ and the receiver resonator 50″ do not exist to simplify the power conditioning concepts, although such concepts are equally applicable to the presence of such resonators (such as in Fig.19A middle). Fig.19A and Fig.19B The system has four independent control parameters that can be adjusted during operation to regulate the power delivered to the receiver module 40" and thereby delivered to the load 70". Typical commercial power conditioning units are generally referred to as "boost converters" by virtue of boosting their output voltage above that of the source voltage. Such devices have only two control parameters.

[0363] A first independent control parameter that may be adjusted during operation to regulate the power delivered to the receiver module 40" and thereby to the load 70" is the oscillation frequency of the power amplifier 26B" which may be adjusted by the controller 22" in the oscillator 26A".

[0364] A second independent control parameter that may be adjusted during operation to regulate the power delivered to the receiver module 40″ and thereby delivered to the load 70″ is the output load on the rectifier 46D of the receiver module 40″. The output load in turn directly determines the input impedance of the rectifier 46D and thereby the input impedance of the receiver module 40″. This in turn is the load seen by the transmitter module 20″ and directly determines the input DC equivalent resistance of the power amplifier 26B″. Manipulation of the output load on the rectifier 46D is under the control of the receiver controller 42″ via the load management system 46E″ of the receiver module 40′ (see Fig.19A ) is completed. This second independent control parameter is a property of the receiver module, but it inherently controls the load seen by the power supply. The control point for manipulating this parameter is the load management system 46E" of the receiver module 40".

[0365] The third and fourth independent control parameters that can be adjusted during operation to regulate the power delivered to the receiver module 40" and thereby delivered to the load 70" are the properties of the rectifier 46D of the receiver module 40" (see Figure 7 ) and the properties of power amplifier 26B″ ( Fig.19A ) and are similar in nature but completely independent of each other. Both the rectifier 46D and the power amplifier 26B" comprise multi-terminal amplifying devices that rely on modulating the passage of current between two terminals of the multi-terminal device by a voltage signal applied to a third terminal of each device. The simplest multi-terminal amplifying device that can be used in each of the rectifier 46D and the power amplifier 26B" is a transistor. This allows a phase difference to exist between a voltage signal and a current signal generated by or in the device. That voltage-current phase difference is adjustable via the applied voltage. The rectifier 46D can be an adjustable phase RF rectifier, the voltage-current phase difference of which can be adjusted via the receiver controller 42". In the case of the power amplifier 26B", the voltage-current phase difference can be adjusted via the transmitter controller 22". The rectifier 46D can effectively comprise a differential self-synchronous RF rectifier. The rectifier 46D can comprise a differential switched mode self-synchronous RF rectifier.

[0366] Fig.19A and 19B An example is based on transmitting power from a solar cell or further from an array of solar cells, wherein the power delivered by the solar cell 420 may vary significantly down to zero depending on the sunlight. There are many other power sources that suffer from variable output in terms of power and in terms of the voltage generated. Such power sources include power generation turbines, wind turbines, and various batteries and storage batteries. Wind turbines can vary significantly in their power generation and various batteries can have a wide range of power consumption curves. In view of the power transmission efficiency of the system, either of the systems 10″ and 410 can be configured to receive power, for example, without restriction from commercial batteries with a slow open circuit voltage decay curve. The load management system 46E″ can be configured to change the input DC equivalent resistance of the power amplifier 26B″ as described above, and the controllers 22″ and 42″ can be configured to provide the required voltage level to the load 70″ until this voltage can no longer be maintained by the power transmitted and the adjustability of the parameters of the systems 10″ and 410.

[0367] Fig.19A and its associated descriptions illustrate near-field wireless power transfer from a single solar cell 420 to a single load 70″ (typically a battery). In actual implementations of larger solar cell power systems, arrays of batteries are typically used, so that the same Fig.12 , Fig.13A and Fig. 13B In a power transmission scheme similar to the above, there are multiple transmitter subsystems and usually a single receiver subsystem. Fig. 20A and 20B This is shown in FIG. 1 , where the solar panel has a transparent solar cover 440 and each solar cell 420 has one near-field wireless transmission subsystem, and thus by way of example includes sixty near-field wireless power transmission subsystems 16, each transmission subsystem 16 including a transmitter resonator 30″, a transmitter module 20″ and a power conditioning unit 430, as shown in FIG. Fig.19A To avoid confusion, the transmitting subsystem 16 is not Fig.19A Indicated in Fig. 20B , 21B and 22B, as further described below.

[0368] In one embodiment, coupling each individual solar cell of a solar panel composed of multiple solar cells to a power delivery and management system allows for cell-level power management. By providing power management at each individual cell, power collection can be optimized for each cell, resulting in improved efficiency of the entire solar panel system. In this embodiment, the effects caused by failure of individual cells or poor connections between cells will be mitigated. Power collection at the individual cell level allows for maximum power harvesting even in less than ideal conditions, such as rain, shadows, or when debris covers a portion of the solar panel.

[0369] To avoid confusion, only Fig. 20B A near-field wireless power transmission subsystem 16 is indicated in FIG. Fig. 20A and 20B In the embodiment, the transmitter resonator 30″ of each transmitter subsystem 16 can be located on the back side of its corresponding solar cell 420. Fig. 20A As seen from the front of the panel in FIG. 1 , the flat area of ​​the solar cell represents the active solar radiation receiving and energy conversion semiconductor device itself, and is correspondingly marked as 420. Fig. 20B As seen from the back in FIG. 1 , the flat area of ​​the device represents a transmitter resonator and is correspondingly labeled 30″. The transmitter resonator 30″ may have a surface area having an extension that may be at least a major portion of the extension of the active solar radiation receiving surface of the solar cell 420. The transmitter module 20″ and the power conditioning unit 430 of each near-field wireless power transmission subsystem 16 are Fig. 20B In order to avoid confusion, the combined component 450 is not shown in FIG. Fig.19A Indicated as a unit and in Fig. 20B ,21B 22B, as further described below. A single receiver resonator 50" may be mounted in a frame 460 of a solar panel 400. A single receiver module 40" may be mounted directly on the back side of the receiver resonator 50".

[0370] In operation, the near-field resonant wireless power transfer system 10" can be used with Fig.12 , Fig.13A and Fig. 13B The near-field resonant wireless power transfer system 10 functions in the same manner as the near-field resonant wireless power transfer system 10, with the difference that the voltage VDD applied to each of the power amplifiers 26B" is replaced by a power signal from a power conditioning unit (PCU) 430, which in turn receives its power from the associated solar cell 420.

[0371] exist Fig. 20A and 20B In another embodiment of the system, the frame 460 can be configured as a receiver resonator suitable for receiving power from all transmitter resonators 30", and the receiver module 40" can be located on the frame 460. In this embodiment, the plate within the frame 460 is not a resonator but can be a simple flat sheet of non-conductive material.

[0372] In another embodiment, respectively Fig.21A and 21B The solar panels 400' shown in the front and rear views of FIG. 400 enable each near-field wireless power transmitter subsystem to transfer power to one near-field wireless power receiver subsystem. Although the frame 460 is shown as being filled with an opaque plate 470, the plate 470 may not be part of the near-field circuit or magnetic circuit. For clarity, the same Fig. 20A and 20B On the receiving side, use Fig.19A Again, to avoid confusion, only one receiving-side device is indicated.

[0373] In operation, Fig.21A and Fig. 21B The solar panel arrangement 400' may have individual transmitter modules 20" linked by hard wires (not shown) so that the transmitter modules can be in phase, thereby minimizing power losses in transmission. In other embodiments, the transmitter modules 20" may be independent and, as in Fig.14 , Fig.17 and Fig.18 It plays a role as explained in it.

[0374] In respectively Fig.22AIn yet a further embodiment of a solar panel arrangement 400" shown in the front view of and the rear view of 22B, an array of twenty-five solar cells arranged, for example, in five rows, with five cells 420 in each row. Each solar cell 420 has at its rear a transmitter resonator 30' including its corresponding transmitter module 20" and a unit 450' including a power conditioning unit 430. At the bottom and top of the array and between every two rows of solar cells are receiver resonators 50" arranged in a plane substantially perpendicular to the plane of the solar cells 420, each receiver resonator 50" being in wired electrical communication with its corresponding receiver module 40". As with the previous solar panel embodiments, one example of each component is labeled. As in Fig. 20A and 20B as well as Fig.21A and 21B As with the embodiment shown in FIG. 4 , in some embodiments, the solar panel arrangement 400 ″ may also have a frame 460 . For clarity, this is not shown in FIG. Fig.22A and 22B Frame 460 is shown in FIG.

[0375] In operation, a transmitter resonator 30″ of a solar cell 420 in a row of the system 400″ transmits power to a receiver resonator 50″ both above and below the transmitter resonator. In this embodiment, however, there is an additional mechanism by which various nearest neighbor receiver resonators 50″ are resonantly coupled and the collected power is shared between the receiver resonators. The collected power gathered by all of the receiver resonators 50″ of the array can therefore be tapped off via any one or more of the various receiver modules 40″. In certain embodiments, the power collected by all of the receiver modules 40″ can, by way of example, be tapped off only via the bottom-most receiver module 40″. Any of the receiver modules 40″ on any receiver resonator 50″ can be used as a receiver module to collect power for a row of solar cells 420, while also functioning as a transmitter module to transmit the collected power via its associated receiver resonator 50″ to another receiver resonator 50″ proximate thereto. This action can be repeated down the array to transfer power to the bottom-most receiver module 40″.

[0376] exist Fig.22A and 22B In another embodiment of the system, around Fig.22A and 22B The solar array is surrounded by a frame (similar to Fig. 20A and 20BThe frame 460) can be a receiver resonator that carries the receiver modules 40' and can receive power from the various receiver resonators 50". In this way, the total power generated by all of the solar cells 420 in the array can be received by the resonator frame 460 and tapped via the receiver modules 40" for further electrical transmission.

[0377] Power collection at the individual solar cell level can be accomplished with a wired connection. However, the use of wireless transmission systems in solar panels allows for a reduction in wiring, and therefore a reduction in manufacturing costs.

[0378] In reference Fig.23 In another embodiment described in the flowchart in , a method

[1500] for transmitting power from a photovoltaic cell 420 to an electrical load 70" is provided, the method comprising: converting

[1510] the power from the photovoltaic cell 420 into an oscillating power signal having an oscillating frequency in a transmitting module 20", transmitting

[1520] the power to a transmitter resonator 30" that is in wired electrical communication with the transmitting module 20" and is configured to resonate at the oscillating frequency; receiving

[1530] the power in a receiver resonator 50", the receiver resonator being configured to Resonating at an oscillating frequency and configured to receive power from a transmitter resonator 30″ via at least one of capacitive coupling and magnetic induction; receiving

[1540] power in a receiver module 40″ in wired electrical communication with a receiver resonator 50″; and providing

[1550] the received power in the form of direct current to an electrical load 70″ via wired electrical communication. The method may further include converting the voltage and current of the power from the photovoltaic cell 420 into a voltage and current suitable for the transmitter module 20″ before converting the power into the oscillating power signal.

[0379] In reference Fig.19A and Fig.24In another embodiment of the method described in the flowchart in , a method

[1600] for transmitting power from an array 400 of photovoltaic cells 420 to an electrical load 70" is provided, the method comprising: in each of a first plurality of corresponding transmitting modules 20", converting

[1610] power from each of the photovoltaic cells 420 in the array 400 into an oscillating power signal having an oscillating frequency; in each of the transmitting modules 20", transmitting

[1620] the power to a corresponding transmitter resonator in a second plurality of transmitter resonators 30", 30″, each of the transmitter resonators being configured to resonate at an oscillation frequency; receiving

[1630] power in a receiver resonator 50″, the receiver resonator being configured to resonate at an oscillation frequency and being arranged to receive power from the plurality of transmitter resonators 30″ via at least one of capacitive coupling and magnetic induction; receiving

[1640] power in a receiver module 40″ in wired electrical communication with the receiver resonator 50″; and providing

[1650] the received power in the form of direct current to an electrical load 70″ via wired electrical communication. The method may further include converting a voltage and a current of power from each photovoltaic cell 420 into a voltage and a current adapted for a corresponding transmit stream module 20″ prior to converting the power into an oscillating power signal. Receiving

[1630] power in a receiver resonator 50″ may include receiving power in a receiver resonator arranged around a planar periphery of an array 400 of photovoltaic cells.

[0380] In reference Fig.19A and Fig.25In another embodiment of the method described in the flowchart in , a method

[1700] for transmitting power from an array 400′ of photovoltaic cells 420 to an electrical load 70″ is provided, the method comprising: converting

[1710] power from each of the photovoltaic cells 420 in the array 400′ into an oscillating power signal having an oscillating frequency in each of a first plurality of corresponding transmitting modules 20″; transmitting

[1720] power from each of the transmitting modules 20″ to a corresponding transmitter resonator 30″ in a second plurality of transmitter resonators 30″, wherein each transmitter resonator 30″ is configured with resonating at an oscillation frequency; receiving

[1730] power from each transmitter resonator 30" in a corresponding receiver resonator 50" configured to resonate at the oscillation frequency, wherein each receiver resonator 50" is further configured and arranged to receive power from the transmitter resonator 30" via at least one of capacitive coupling and magnetic induction; receiving

[1740] power from each receiver resonator 50" in a corresponding receiver module 40" in wired electrical communication with the receiver resonator 50"; and providing

[1750] the received power in the form of direct current to an electrical load 70" via wired electrical communication. The method may further include converting a voltage and current of power from each photovoltaic cell 420 into a voltage and current suitable for a corresponding transmitter module 20" before converting the power into an oscillating power signal.

[0381] In reference Fig.19A and Fig.26 In another embodiment described in the flowchart of FIG. 1 , a method for transmitting power from an array 400″ of photovoltaic cells 420 to an electrical load 70″ (at Fig.19AA method

[1800] is provided for transmitting power from each of the photovoltaic cells 420 in the array 400" to an oscillating power signal having an oscillation frequency in each of a first plurality of corresponding transmitting modules 20", transmitting

[1820] the power from each of the transmitting modules 20" to a transmitter resonator 30" in a second plurality of transmitter resonators 30", wherein each transmitter resonator 30" is configured to resonate at the oscillation frequency; receiving

[1830] the power from each transmitter resonator 30" in any proximate receiver resonator 50" in a third plurality of receiver resonators 50", wherein the receiver resonators are configured to resonate at the oscillation frequency, wherein the power from each of the transmitting modules 20" is transmitted to a transmitter resonator 30" in a second plurality of transmitter resonators 30", wherein each transmitter resonator 30" is configured to resonate at the oscillation frequency, wherein the power from each transmitter resonator 30" is received in any proximate receiver resonator 50" in a third plurality of receiver resonators 50", wherein the receiver resonators are configured to resonate at the oscillation frequency, wherein the power from each transmitter resonator 30" is received in any proximate receiver resonator 50" in a third plurality of receiver resonators , each receiver resonator 50" is further configured and arranged to receive power from the transmitter resonator 30" via at least one of capacitive coupling and magnetic induction; share

[1840] the received power among a third plurality of receiver resonators 50"; and provide

[1850] the received power in the form of direct current to an electrical load 70" via wired electrical communication, wherein the received power comes from one or more of the third plurality of receiver resonators 50" via corresponding one or more receiver modules 40". The method may further include converting the voltage and current of the power from each photovoltaic cell 420 into a voltage and current suitable for the corresponding transmitter module 20" before converting the power into an oscillating power signal.

[0382] Fig.27A A representative portion 500 of an expanded near-field wireless power distribution system in an electric vehicle having a conductive chassis 510 is shown. Fig.19A In the embodiment of the general system 10″, the power source is a rechargeable battery 520 instead of a solar cell 420, and the load 70″ is an electric motor 530 instead of a Fig.19A The battery in the Fig.14 The system shown in A may optionally include: Fig.19A In other embodiments, the transmitter modules may act in conjunction to provide the power conditioning unit 430 described above. Fig.19B The power regulation described.

[0383] exist Fig.27A The system shown in and described in more detail below can operate by capacitive power transfer, inductive power transfer, or by bimodal power transfer. Figure 4B and Fig.19A , the transmitter resonator 30″ includes a dielectric element 138 sandwiched between conductive antennas 132 and 134. Referring to Figure 4B and Fig.19A, the receiver resonator 50" includes a dielectric element 158 ​​clamped between conductive antennas 152 and 154. The transmitter module 20" is shown mounted directly to the antenna 132, which also acts as a frame or support for the battery 520. The transmitter module 20" can be electrically connected between the battery 520 and the transmitter resonator 30". The receiver module 40" is shown mounted directly to the electric motor 530. The receiver module 40" can be electrically connected between the receiver resonator 50" and the electric motor 530.

[0384] Fig.27B A representative portion 500 of an expanded near-field wireless power distribution system in an electric vehicle having a conductive chassis 510 is shown. Fig.19A In the embodiment of the general system 10″, again as Fig.27A In the embodiment, the power source is a rechargeable battery 520 instead of a solar cell 420, and the load 70" is an electric motor 530 instead of a Fig.19A The battery in the Fig.27B The system shown in the figure may optionally include the following: Fig.19A In other embodiments, the transmitter module 20″ and the receiver module 40″ can work together to provide the power conditioning unit 430 in the above reference. Fig.19B The power regulation described.

[0385] exist Fig.27B The system shown in and described in more detail below can operate by capacitive power transfer, inductive power transfer, or by bimodal power transfer. Figure 4B and Fig.19A , the transmitter resonator 30″ includes a dielectric element 138 sandwiched between conductive antennas 132 and 134. Referring to Figure 4B and Fig.19A , the receiver resonator 50″′ comprises Fig.27A The dielectric element 158 ​​and the conductive antenna 152 and antenna 154 are shown, and in this embodiment, there is no receiver resonator 50'". The transmitter module 20" is shown mounted directly to the antenna 132, which also acts as a frame or support for the battery 520. The transmitter module 20" can be electrically connected between the battery 520 and the transmitter resonator 30". The receiver module 40" is shown mounted directly to the electric motor 530. In this embodiment, the receiver module 40" can be electrically connected between the electric motor 530 and the chassis 510. In this arrangement, there is sufficient coupling between the chassis 510 and the antenna 152 for suitable and efficient power transfer. The conductive mechanical components of the system (i.e., components having, for example, a load-bearing structural function in the system) can thereby form part of the resonant structure of the power transfer system.

[0386] exist Fig.27A and27B In the embodiment shown in , specifically, the focus is on power supplied to an electric motor 530 to drive one of the vehicle's wheels, but an equivalent arrangement may be implemented for any electrical subsystem on the vehicle using multiple suitably adapted receiver modules 40", with a transmitter module 20" providing power to all receiver modules.

[0387] For transferring power from the battery to the electrical subsystems of the vehicle Fig.27A and Fig.27B The arrangement is used to a large extent to avoid the extremely complex automotive wiring harnesses that cause difficulties during vehicle manufacturing and are a source of considerable manufacturing costs. Fig.27A and Fig.27B The embodiments in, together with their extension to other electrical subsystems of a vehicle, may be described as an "extended near-field wireless power distribution system."

[0388] In addition to the other wheels of the electric vehicle, the arrangement can be extended to headlights and other vehicle accessories, including without limitation interior lights, dashboard displays, gauges, digital electronics, navigation systems, warning systems, etc. The application is not limited to electric vehicles. It can be applied to hybrid or internal combustion vehicles to distribute power as needed and when needed. It can be similarly applied to other vehicles that employ any electrical system that requires power. Examples include without limitation motorized or non-motorized bicycles, aircraft, boats, and other vehicles that employ on-board power. The battery or power source need not be limited to being on the vehicle. About Figures 1 to 11 The principles described in 19A and 19B and 27A and 27B are also applicable to fixed and vehicle-mounted systems that require power from a geostationary source (e.g., a fixed orbit that can be used indefinitely to supply power to mobile vehicles).

[0389] Fig.28A Show Fig.19A Another embodiment of the universal system 10″ in the power supply system 600, the power supply system is used to use the power supply system according to Figure 1 And in more detail according to Figure 6 The primary side 12 of the computer monitor 610 located on the table top 620 of the table supplies power from a suitable source. Fig.19A The transmitter module 20″ and the transmitter resonator 30″ are both incorporated into the primary side 12. In the arrangement of the system 600, according to Fig.19A The receiver resonator 50″ forms the base of the monitor 610. Fig.19A The receiver module 40" may be incorporated into the base of the monitor 610. Alternatively, Fig.19A The receiver module 40" may be incorporated into the monitor 610 itself. Figure 4B , antenna 152 forms the bottom of the base of monitor 610 and is separated from antenna 154 by dielectric element 158.

[0390] The housing and structural frame 630 of the monitor 610 may be at least partially conductive and act as a continuous conductor to transmit data via the receiver module 40″ (see Fig.19A ) supplies the power signal from antenna 154 to the Fig.19A The circuitry of the monitor 610 of the load resonator 70″ is connected to the monitor 610. Other electrical connectors from the antenna 152 to the circuitry of the monitor 610 extend upward from the antenna 152 along the base of the monitor 610. In other embodiments, the housing and structural frame 630 of the monitor 610 can be a non-conductive polymer and a separate conductor extends from the antenna 154 to represent Fig.19A The load resonator 70″ is a circuit of the monitor 610.

[0391] If used to Fig.28B As shown in another embodiment of a power supply system 600′ for supplying power to a computer monitor 610 in FIG. 1 , the base of the monitor 610 may include only the antenna 152 and the dielectric element 158. In this embodiment, the metal conductive portion of the monitor housing or frame 630 acts as the antenna instead of the antenna 154, and the housing or frame 630 has sufficient coupling with the antenna 152 under the dielectric element 158 ​​to provide sufficiently efficient power transfer. Fig.19A The receiver module 40" may be incorporated into the base of the monitor 610. Alternatively, Fig.19A The receiver module 40" can be incorporated into the monitor 610 itself. The housing and structural frame 630 of the monitor 610 can act as a continuous electrical conductor to supply the power signal to the display via the receiver module 40". Fig.19A The load resonator 70″ is a circuit of the monitor 610.

[0392] The system 600 may optionally include: Fig.19A In some embodiments, the transmitter module 20″ and the receiver module 40″ can work together to provide a near-field wireless power transmission as shown in FIG. Fig.19A The power regulation described. Fig.28A The near-field wireless power transfer system of removes the need for cumbersome cables to supply power to the monitor 610 and employs the mechanical structural elements of the system as integral electrical / electronic components in the power transfer arrangement.

[0393] As reference Fig.29 The flowchart and Fig.19A and Fig.19BAccording to the system, a method

[2000] for transmitting power from a DC power source 420 to an electrical load 70" is provided, the method comprising: providing

[2010] an electric power transmission system 10", 410 for performing wired electrical communication with the power source 420, the electric power transmission system 10", 410 comprising: an oscillator 26A" capable of oscillating at an oscillation frequency, a power amplifier 26B" and a transmitter tuning network 28" both under the control of a transmitter controller 22", and a receiver tuning network 48" and a load management system 46E" both under the control of a receiver controller 42", wherein the load management system 46E" is in wired electrical communication with the electrical load 70"; in the power amplifier 26 B″ converts

[2020] the power from the power supply 420 into an oscillating power signal having an oscillating frequency; transmits

[2030] the power signal from the power amplifier 26B″ to the load management system 46E″ via the transmitter tuning network 28″ and the receiver tuning network 48″ under the control of the transmitter controller 22″; adjusts

[2040] at least one of the oscillation frequency, the input DC equivalent resistance of the power amplifier 26B″, the transmitter tuning network 28″, the receiver tuning network 48″ and the load management system 46E″ to change the rate of power transmission; and provides

[2050] the power received by the load management system 46E″ in the form of direct current to the power load 70″ via wired electrical communication.

[0394] Transmitting

[2030] a power signal via the transmitter tuning network 28″ and the receiver tuning network 48″ may include transmitting power by wired communication or by wireless communication. Transmitting power by wireless communication may include transmitting power by near-field wireless communication. Transmitting power by near-field wireless communication may include transmitting power by at least one of capacitive coupling and inductive coupling. Transmitting power from a DC power source 420 may include transmitting power from at least one solar cell 420. Transmitting power from a DC power source may include transmitting power from at least one battery. Transmitting power from a DC power source may include transmitting power from a power source having a varying voltage.

[0395] In reference Fig.30 and consider more deeply Fig.19A and Fig.19B In another embodiment of the system described herein, a method

[2100] for transmitting power from a DC power source 420 to an electrical load 70" is provided, the method comprising: providing

[2110] a power transmission system 10", 410 in wired electrical communication with the power source 420, the power transmission system 10", 410 including an adjustable phase radio frequency rectifier 46D (see Figure 7) an RF power amplifier 26B″ for RF communication, the adjustable phase RF rectifier being in wired electrical contact with an electrical load 70″; converting

[2120] power from a DC power supply 420 into an RF oscillating power signal in the power amplifier 26B″; converting

[2130] the RF oscillating power signal into a DC power signal in the rectifier 46D; and adjusting

[2140] the efficiency of power transmission by adjusting the current-voltage phase characteristic of the rectifier 46D. Providing an adjustable phase RF rectifier may include providing a differential self-synchronous RF rectifier 46D.

[0396] The method

[2100] may further include adjusting the efficiency of power transmission by adjusting the DC equivalent input resistance of the power amplifier 26B". Providing

[2110] the power transmission system 10", 410 may include providing a load management system 46E" for wired communication between the rectifier 46D and the load 70". Adjusting the DC equivalent input resistance of the power amplifier 26B" may include adjusting the input impedance of the rectifier 46D by adjusting the load management system 46E". Adjusting the load management system 46E" may include automatically adjusting the load management system 46E".

[0397] The method

[2100] may further include adjusting the efficiency of the power transmission by adjusting the current-voltage phase characteristic of the power amplifier 26B". Providing

[2110] the power transmission system 10", 410 may include providing a transmitter controller 22" that communicates with the power amplifier 26B" to control the power amplifier 26B". Adjusting the current-voltage phase characteristic of the power amplifier 26B" may be performed by the transmitter controller 22". Adjusting the current-voltage phase characteristic of the power amplifier 26B" may be performed automatically by the transmitter controller 22".

[0398] The method

[2100] may further include adjusting the efficiency of power transfer by changing the oscillation frequency of the power amplifier 26B″.

[0399] Providing

[2110] the power transmission system 10", 410 may include providing a receiver controller 42" that communicates with the rectifier 46D to control the rectifier 46D. Adjusting the current-voltage phase characteristic of the rectifier 46D may be performed by the receiver controller 42". Adjusting the current-voltage phase characteristic of the rectifier 46D may be performed automatically by the receiver controller 42".

[0400] Providing

[2110] the power delivery system 10", 410 may include providing direct wired RF communication (via Fig.19BA power amplifier 26B" is provided that is connected to a power amplifier 26B" 60" of the power transmission system 10", 410. The power transmission system 10", 410 may include providing a power amplifier 26B" for wireless near-field RF communication with an adjustable phase RF rectifier 46D.

[0401] Providing

[2110] the power delivery system 10″, 410 may include providing 50 for wired radio frequency communication with the power amplifier 26B′

[0402] 30″ and a receiver resonator 50″ for wired RF communication with the RF rectifier 46D. The method

[2100] may further include operating the transmitter resonator 30″ and the receiver resonator 50″ for wireless near-field RF communication with each other. Providing

[2110] the power transfer system 10″, 410 may include providing a power amplifier 26B″ for at least one of capacitive near-field wireless RF communication and inductive near-field wireless RF communication with the rectifier 46D. Providing

[2110] the power transfer system 10″, 410 may include providing a power amplifier 26B″ for dual-peak wireless near-field communication with the rectifier 46D.

[0403] The method

[2100] may further include: providing a power conditioning unit 430 electrically disposed between the power source 420 and the power transmission system 10"; and adjusting the power conditioning unit 430 to adjust at least one of the current and the voltage from the power source 420 to improve the efficiency of power transmission.

[0404] Based on Fig.19A and Fig.19B A more in-depth consideration of the system and reference Figure 7 , a universal power transmission system 10", 410 for supplying power from a DC power source 420 to an electrical load 70" includes: an RF power amplifier 26B", which is in wired electrical communication with the power source 420 and is configured to convert the DC voltage from the power source 420 into an AC voltage signal having an oscillating frequency; an adjustable phase RF rectifier, which is in wired electrical contact with the electrical load 70" and in RF communication with the power amplifier, the rectifier being configured to receive power transmitted from the power amplifier 26B"; and a receiver controller 42", which is in communication with the rectifier 46D, the receiver controller being configured to adjust the efficiency of power transmission from the power amplifier 26B" to the rectifier 46D by adjusting the current-voltage phase characteristic of the rectifier 46D. The receiver controller 42" can be configured to automatically adjust the current-voltage phase characteristic of the rectifier 46D. The rectifier can be a differential self-synchronous RF rectifier.

[0405] The power transmission system 10″, 410 may further include a load management system 46E″, which is in wired communication with the load 70″ and is arranged between the load 70″ and the rectifier 46D in a power signal manner, and the load management system 46E″ is configured to increase the efficiency of power transmission by adjusting the input impedance of the rectifier 46D. The load management system 46E″ can be configured to automatically adjust the input impedance of the rectifier 46D.

[0406] The power transmission system 10″, 410 may further include a transmitter controller 22″ in communication with the power amplifier 26B″, the transmitter controller 22″ configured to increase the efficiency of power transmission by adjusting the current-voltage phase characteristic of the power amplifier 26B″. The transmitter controller 22″ may be configured to automatically adjust the current-voltage phase characteristic of the power amplifier 26B″ to increase the efficiency of power transmission.

[0407] The power transfer system 10", 410 may further include an oscillator 26A" in communication with the power amplifier 26B" and the transmitter controller 22". The transmitter controller 22" may be configured to adjust the oscillation frequency via the oscillator 26A".

[0408] The power amplifier 26B" can be in direct wired RF communication with the adjustable phase RF rectifier 46D (via Fig.19B connection 60″). The power amplifier 26B″ can perform wireless near-field RF communication with the adjustable phase RF rectifier 46D. The power transmission system 10″, 410 may include a transmitter resonator 30″ for wired RF communication with the power amplifier 26B″ and a receiver resonator 50″ for wired RF communication with the rectifier 46D. The transmitter resonator 30″ and the receiver resonator 50″ can perform wireless near-field RF communication with each other. The power amplifier 26B″ can perform at least one of capacitive near-field wireless RF communication and inductive near-field wireless RF communication with the rectifier 46D. The power amplifier 26B″ can perform dual-peak near-field wireless RF communication with the rectifier 46D.

[0409] The power transfer system may further include a power conditioning unit 430 electrically disposed between the power source 420 and the power amplifier 26B″, the power conditioning unit 430 being configured to adjust at least one of the current and the voltage from the power source 420 to improve the efficiency of the power transfer.

[0410] In reference Fig.19A , Fig.19B , Fig.27A and 27B ,as well as Fig.28A and 28BIn another embodiment, an electric system includes: a mechanical load bearing structure 510, 630 having a conductive first portion; an electrical load; and a power transfer system 10", 410, including at least one radio frequency resonator 30", 50" configured for near-field wireless power transfer, wherein the resonator at least partially includes the conductive first portion. The electric system may further include a rechargeable battery 520, and the electrical load may include an electric motor 530. The electric system may be an electric vehicle 500, 500', and the mechanical load bearing structure may include a chassis 510 of the vehicle. The electric system may be a display monitor 610 and the mechanical load bearing structure may be at least one of a frame 630 and a base of the monitor.

[0411] The electric system may further include a power supply. The power transmission system may include: an RF power amplifier 26B″, which is in wired electrical communication with the power supply and is configured to convert a DC voltage from the power supply into an AC voltage signal having an oscillating frequency; an adjustable phase RF rectifier 46D, which is in wired electrical contact with the power load 70″ and in RF communication with the power amplifier 26B″; a rectifier 46D, configured to receive power transmitted from the power amplifier 26B″; and a receiver controller 42″, which is in communication with the rectifier 46D, and the receiver controller 42″ is configured to adjust the efficiency of power transmission from the power amplifier 26B″ to the rectifier 46D by adjusting the current-voltage phase characteristics of the rectifier 46D.

[0412] In another embodiment, as in Fig.19A and 19B , Fig.27A and 27B ,as well as Fig.28A and 28B As described in the specification, an apparatus comprises: a mechanical load bearing structure 510, 630 having a conductive first portion; a power source; an electrical load 70", 530, 610; and a power transmission system 10", 410, comprising: an RF power amplifier 26B", which is in wired electrical communication with the power source and is configured to convert a DC voltage from the power source into an AC voltage signal having an oscillating frequency; an adjustable phase RF rectifier 46D, which is in wired electrical contact with the electrical load 70" and in RF communication with the power amplifier 26B", a rectifier 46D configured to receive power transmitted from the power amplifier 26B", and a receiver controller 42", which is in communication with the rectifier 46D, the receiver controller 42" being configured to adjust the efficiency of power transmission from the power amplifier 26B" to the rectifier 46D by adjusting the current-voltage phase characteristic of the rectifier 46D; wherein the conductive first portion is configured to carry at least one of an RF signal from the power amplifier 26B" and an RF signal to the rectifier 46D.

[0413] The device may further include a load management system 46E″, which is in wired communication with the load 70″ and is arranged between the load 70″ and the rectifier 46D in a power signal manner, and the load management system 46E″ is configured to increase the efficiency of power transmission by adjusting the input impedance of the rectifier 46D. The device may further include a transmitter controller 22″ that communicates with the power amplifier 26B″, and the transmitter controller 22″ is configured to increase the efficiency of power transmission by adjusting the current-voltage phase characteristic of the power amplifier 26B″. The device may further include an oscillator 26A″ that communicates with the power amplifier 26B″ and the transmitter controller 22″, wherein the transmitter controller 22″ is configured to adjust the oscillation frequency via the oscillator 26A″.

[0414] The power amplifier 26B″ can perform direct wired RF communication with the rectifier 46D via the conductive first portion. The power amplifier 26B″ can perform wireless near-field RF communication with the rectifier 46D. The power transmission system 10″, 410 may include a transmitter resonator 30″ for wired RF communication with the power amplifier 26B″ and a receiver resonator 50″ for wired RF communication with the rectifier 46D, and one of the transmitter resonator 30″ and the receiver resonator 50″ may include the conductive first portion. The transmitter resonator 30″ and the receiver resonator 50″ can perform wireless near-field RF communication with each other. The power amplifier 26B″ can perform at least one of capacitive near-field wireless RF communication and inductive near-field wireless RF communication with the rectifier 46D. The power amplifier 26B″ can perform bimodal near-field wireless RF communication with the rectifier 46D. The DC power source may include a rechargeable battery 520, and the load may include an electric motor 530.

[0415] exist Fig.32 It is schematically shown in and based on Figure 6 , Figure 7 , Figure 8 and Fig. 9In another embodiment of the present invention, a sealed bidirectional power transmission circuit device 800 is provided, wherein the device has a plurality of terminals configured to electrically communicate with a device outside the sealed device 800, wherein the sealed device 800 includes within its sealed interior: a multi-terminal power switching (MPS) device 810 having at least one DC terminal, at least one AC terminal, and at least one control terminal, wherein the MPS device 810 is adjustable between an amplification state and a rectification state, and is configured to bidirectionally transmit a DC voltage and a DC current via at least one DC terminal, and to bidirectionally transmit a DC voltage and a DC current via at least one AC terminal. The PFDCA circuit 820 is configured to establish a radio frequency oscillation signal having a frequency and a phase of the radio frequency power signal at at least one control terminal of the MPS device 810, and adjust the MPS device 810 between an amplification state and a rectification state by adjusting the phase of the radio frequency oscillation signal under the instruction of the controller 880. The PFDCA circuit 820 may be further configured to establish a duty cycle of the radio frequency oscillation signal. The PDFCA circuit 820 may include a radio frequency oscillator for generating a radio frequency oscillation signal under the instruction of the controller 880. The term "multi-terminal power switching device" is used herein to describe a device having at least three terminals and capable of switching or modulating a current flowing between at least two terminals of the device based on a signal applied to at least one third terminal of the device. Suitable MPS devices 810 include, but are not limited to, mechanical relay switches, solid-state switches, electro-optical switches (also known as optical switches), thyristors, waveguide switches, transistors (including, for example, MOSFETs, MESFETs, III-V group semiconductor transistor devices, and BJT devices), and power tube devices (including, for example, triodes and pentodes).

[0416] In some embodiments, the circuit is sealed with a polymeric coating or mold to form a seal or sealed device. In some embodiments, the sealed device protects components disposed on the interior of the device. In some embodiments, the seal of the device provides electrical insulation to prevent static discharge, short circuits, or other harmful discharges that can damage components of the device. In some embodiments, the sealed device protects internal components from oxidation. In some embodiments, the seal can form a waterproof barrier or a water vapor barrier. In some embodiments, the seal provides an electrical connection that facilitates the device by providing access to one or more terminals on the exterior of the sealed device.

[0417] The sealed power transmission circuit device 800 may further include a tuning network 830 in wired data communication with the controller 880 inside the seal, the tuning network being in wired electrical communication with the MPS device 810 via at least one AC terminal, the tuning network 830 being configured to adjust the RF power signal to a tuned RF power signal from the tuning network 830 under instructions from the controller 880 when the MPS device 810 is in an amplification state. The tuning network 830 may include Figure 8 and Fig. 9 A harmonic termination network circuit of the type shown in is configured to suppress harmonics of a radio frequency oscillation signal in a radio frequency power signal. Figure 8 and Fig. 9 As shown in , the harmonic termination network may include one or more inductors and one or more of the first harmonic termination 127I, 147G, the second harmonic termination 127H, 147F, and the third harmonic termination 127F, 147D.

[0418] The sealed power transmission circuit device 800 may include an amplitude / frequency / phase detector (AFPD) 840 in wired data communication with the controller 880 inside the seal, the amplitude / frequency / phase detector being arranged to be in wired electrical communication with the tuning network and configured to determine the amplitude, frequency and phase of any RF power signal transmitted between the tuning network and the AC load / source outside the sealed device. To this end, according to Fig.32 AFPD 840 measures the amplitude, frequency and phase of the signal at the output of tuning network 830 derived from device 800. PFDCA circuit 820 is configured to receive instructions from controller 880 based on the measurement data transmitted to controller 880 by AFPD 840. Fig.32 In other embodiments shown in , the PFDCA circuit 820 is configured to adjust the RF oscillation signal and / or at least one of the DC current and the DC voltage based on a feedback signal received directly from the AFPD 840.

[0419] The tuning network 830 may include a voltage-current tuner for adjusting the phase difference between the voltage and current of the tuned RF signal based on the measurement data from the AFPD 840 when the power switching device is in the amplification condition. Figure 6 A suitable voltage-current tuner is described in more detail. Fig.32 , the voltage-current tuner of the tuning network 830 is applied to the signal connected to the signal derived from the device 800. Fig.32 The voltage-current tuner thus acts as a tuner when transmitting power downward in the Fig.32The power transmitted by the device 800 in the opposite upward direction can be transparent, and the power transmission circuit device 800 is bidirectional. In some embodiments, the tuning network 830 can transmit a tuned RF power signal to the AC load / source 900, which can be the transmitter resonator 30 and 30", as shown in reference Figure 6 as well as Fig.19A , 27A When the AC load / source 900 is this dual peak emitter resonator, a voltage-current tuner can be used to adjust the ratio of the electric field to the magnetic field, as described in reference Figure 6 described.

[0420] The sealed power transmission circuit device 800 may further include a power management (PM) circuit 860 in wired data communication with the controller 880 inside the seal and in wired electrical communication between the MPS 810 and the DC source / load 700 outside the sealed device 800, the power management (PM) circuit being configured to impedance match the MPS 810 with the external DC source / load 700 and to adjust the DC power transmitted between the MPS 810 and the DC source / load 700 based on the measurement data transmitted to the controller by the AFPD 840. Fig.32 In other embodiments shown in , PM circuit 860 may be configured to adjust the DC power transmitted between MPS 810 and DC source / load 700 based on feedback signals received directly from AFPD 840 and / or VID 850 .

[0421] It should be noted again that DC power can be transmitted in both directions through the PM circuit 860 between the MPS 810 and the DC source / load 700. It should also be noted that a convention is maintained herein whereby the DC source / load 700 is described as a "source / load" and the external AC load / source 900 that transmits AC power to the tuning network is described as a "load / source", thereby emphasizing the following point: when the DC source / load 700 functions as a DC power source, the AC load / source 900 functions as a load for said power to be converted into AC power, and vice versa. When the MPS 810 is in either of its amplifying state and rectifying state, in Fig.32 The arrows shown in FIG. 8 near and parallel to the connector indicate the path and direction of the power delivery circuit device 800. When the MPS 810 is in the amplified state, the power flows through Fig.32 Downward; when the MPS 810 is in the rectifying state, power flows through Fig.32 up.

[0422] The sealed power delivery circuit device 800 may further include a voltage / current detector (VID) 850 in wired data communication with the controller 880 inside the seal, the voltage / current detector being configured to determine the DC voltage and DC current transmitted between the MPS 810 and the PM circuit 860. When the MPS 810 is in an amplifying state, the power delivery circuit device 800 may be adjusted based on the measurement result of the VID 850 so that the device 800 presents an equivalent DC load to the DC source / load 700 to allow maximum power to be extracted from the DC source / load 700. The DC voltage at at least one DC terminal of the MPS device 810 is thereby adjusted. When the MPS 810 is in a rectifying state, the power delivery circuit device 800 may be adjusted based on the measurement result of the VID 850 so that the device 800 presents an equivalent DC source impedance to the DC source / load 700 to allow maximum power transmission from the device 800 to the DC source / load 700. The DC voltage at the wired connection between the device 800 and the DC source / load 700 is thereby adjusted.

[0423] The sealed power delivery circuit device 800 may further include a memory 870 in wired data communication with the controller 880, the AFPD 840, and the VID 850 inside the seal, wherein the memory 870 is configured to receive and store signal data from the two detectors 840 and 850 and provide signal data from the two detectors 840 and 850 to the controller 880. The memory 870 is capable of storing the complete state of the device 800 for a series of consecutive instants in time.

[0424] The tuning network may further include one or more of a compensation network, a matching network, and a filter. Figure 6 The compensation network 26E, matching network 26D and filter 26C are suitable for this purpose, and the selection is not limited to Figure 6 device.

[0425] The sealed power delivery circuit device 800 may include a controller 880 within the sealed interior. In other embodiments, the sealed power delivery circuit device 800 may employ an external controller having suitable input / output facilities to communicate data with the various circuits incorporated within the sealed interior of the device 800, and suitable software or firmware may be programmed into the controller to perform all of the control program steps described above.

[0426] The sealed power transfer circuit device 800 may further include at least one communication circuit 890 that functions on one or more of Bluetooth, WiFi, Zigbee, and cellular technologies to bidirectionally transfer information between the controller 880 and devices external to the sealed power transfer circuit device 800. The at least one communication circuit 890 may be in bidirectional wired communication with one or more suitable antennas 894. Although one or more antennas 894 may be disposed within the sealed interior of the device 800, it is typically more effective to dispose the antennas outside the device 800. One or more of the external devices may be other power transfer circuit devices, including, for example, other devices 800, and one or more of the other devices may form a communication circuit as described above in other embodiments (e.g., Figure 1 ) is a part of the collective power transmission system described in ).

[0427] The PFDCA circuit may be arranged to adjust the duty cycle of the RF oscillating signal based on the measurements made by the AFPD 840 and the VID 850. In certain embodiments, information regarding the measurements may be communicated to the controller 880 and from the controller to the PFDCA circuit 820, which then adjusts the duty cycle of the RF oscillating signal based on the received information. Fig.32 In other embodiments shown in , feedback signals may be communicated directly from the AFPD 840 and the VID 850 to the PFDCA circuit 820, which then adjusts the duty cycle of the RF oscillating signal based on the received feedback signals. By changing the duty cycle of the RF oscillating signal, the PFDCA circuit 820 may adjust the direction of power flow through the device 800. When power flows from the DC source / load 700 through the device 800 to the AC load / source 900, the PFDCA circuit 820 may thereby adjust the DC power delivered by the source / load 700 to the device 800 and the AC power delivered from the device 800 to the AC load / source 900. When power flows from the AC load / source 900 through the device 800 to the DC source / load 700, the PFDCA circuit 820 may thereby adjust the AC power delivered by the C load / source 900 to the device 800 and the power delivered by the device 800 to the DC source / load 700.

[0428] The controller 880 can communicate with external devices and circuits 898 disposed outside the sealed interior of the device 800 (in Fig.32 For example, without limitation, such wired communication may be used to exchange data with respect to a system in which the device 800 may be incorporated or to supply a system clock synchronization signal to the controller 880.

[0429] refer to Figure 6 and Figure 7, sensors and detectors 24A, 24B, 24C and 24D can be effectively arranged outside the sealed interior of de...

Claims

1. A system for transmitting power from at least one DC power source to a variable load, It is characterized in that The system comprises: a corresponding high frequency power module disposed proximate to and in electrical communication with each of the at least one DC power source; and a single aggregator configured to receive power from the corresponding at least one DC power source via all at least one high frequency power modules, in: Each of the at least one high frequency power module includes a high frequency (HF) switching signal generator and a pair of differential self-synchronous RF rectifier / amplifiers, a pair of rectifier / amplifiers both in wired electrical communication with the DC power source corresponding to the at least one high frequency power module and configured to extract power from the corresponding DC power source, and The high frequency switching signal generator is configured to provide a switching signal to a corresponding pair of differential self-synchronous radio frequency rectifiers / amplifiers.

2. A circuit for transferring power from at least one DC power source to a variable load, It is characterized in that The circuit comprises: a high frequency power module for each DC power source, each high frequency power module having a power output, each high frequency power module including a high frequency signal generator and a pair of differential self-synchronous RF rectifier / amplifiers, the high frequency switching signal generator being configured to provide a switching signal to a corresponding pair of differential self-synchronous RF rectifier / amplifiers, each differential self-synchronous RF rectifier / amplifier having a wired connection to a corresponding one of the at least one DC power source; and A single aggregator is configured to receive power output from the corresponding at least one DC power source via all of the at least one high frequency power modules.

3. A system according to claim 1 or a circuit according to claim 2, It is characterized in that All of the high frequency power modules are phase locked to each other.

4. A system or circuit as claimed in any preceding claim, It is characterized in that All of the at least one high frequency power modules are mutually phase locked to an AC power signal in the variable load via a phase locked loop.

5. A system or circuit as claimed in any preceding claim, It is characterized in that The phase-locked loop is incorporated into the corresponding high-frequency power module.

6. A system or circuit as claimed in any preceding claim, It is characterized in that Each of the at least one high frequency power module includes a high frequency link that is in wired electrical communication with both differential self-synchronous RF rectifier / amplifiers to receive and mix power signals from the two differential self-synchronous RF rectifier / amplifiers and transmit a mixed power signal on a wired basis.

7. A system or circuit as claimed in any preceding claim, It is characterized in that Each of the at least one high frequency power module includes a switch mode rectifier that is in wired electrical communication with the high frequency link, wherein the switch mode rectifier is configured and arranged to receive the mixed power signal and rectify the mixed power signal and transmit a rectified power signal on a wired basis.

8. A system or circuit as claimed in any preceding claim, It is characterized in that Each of the at least one high frequency power module includes an unfolding circuit that is configured and arranged to receive the rectified power signal from the switch mode rectifier, to unfold the rectified power signal, and to transmit an unfolded power signal on a wired basis.

9. A system or circuit as claimed in any preceding claim, comprising a bimodal wireless near-field high frequency link system, It is characterized in that Each of the at least one high frequency power module includes a primary side of the high frequency link system in wired electrical communication with both of the differential self-synchronous radio frequency rectifier / amplifiers in the at least one high frequency power module; The system includes a single collective secondary side of the high frequency link system configured to receive power from all at least one high frequency link primary side; and The secondary side includes a single receiver resonator and a single receiver module.

10. A system or circuit as claimed in any preceding claim, It is characterized in that The receiver module is included in the aggregator together with a switch mode rectifier and an unfolding circuit, wherein, The switch-mode rectifier is in wired electrical communication with the receiver module and the unfolding circuit to receive a mixed power signal from the receiver resonator and rectify the mixed power signal, and The unfolding circuit is in wired electrical communication with a connection unit and is configured to receive and unfold a rectified power signal from the rectifier and provide the rectified power signal to the variable load.

11. A system or circuit as claimed in any preceding claim, It is characterized in that The switching signals provided by the high frequency switching signal generator to the two differential self-synchronous radio frequency rectifiers / amplifiers differ from each other by one of a predetermined frequency difference and a predetermined phase difference.

12. A system or circuit as claimed in any preceding claim, comprising a controller, in, The controller is configured to transmit at least one of a frequency and a phase determined by the controller based on information about the load and about the DC source to the high-frequency switching signal generator.

13. A system or circuit as claimed in any preceding claim, It is characterized in that The high frequency power module includes the controller.

14. A system or circuit as claimed in any preceding claim, It is characterized in that The at least one DC source is a photovoltaic cell and the system comprises: a planar transparent solar cover having a planar first solar cover surface and a planar second solar cover surface; and a frame for mounting the transparent solar cover, Wherein, at least one of the photovoltaic cells is arranged on the first solar cover surface, and a planar photosensitive surface of at least one of the photovoltaic cells faces the first solar cover surface.

15. A system or circuit as claimed in any preceding claim, It is characterized in that Each high frequency power module includes a high frequency power circuit located on a printed circuit board and in wired electrical communication with the corresponding at least one photovoltaic cell.

16. A system or circuit as claimed in any preceding claim, It is characterized in that The high frequency power circuit is disposed on a plane surface of the printed circuit board facing away from the surface of the first solar cover.

17. The system or circuit of any preceding claim, It is characterized in that A conformal encapsulation layer is included, which is bonded to the first solar cover surface and covers at least one of the photovoltaic cells and the corresponding high-frequency power module.

18. A system or circuit as claimed in any preceding claim, It is characterized in that The invention further comprises a dielectric protection cap located above the high frequency power circuit.

19. A system or circuit as claimed in any preceding claim, It is characterized in that The protective cap is disposed over the conformal encapsulation layer.

20. A system or circuit as claimed in any preceding claim, It is characterized in that The protective cap is disposed below the conformal encapsulation layer.

21. A system or circuit as claimed in any preceding claim, It is characterized in that A perimeter of the protective cap is disposed below the conformal encapsulation layer and sealed to the conformal encapsulation layer, wherein the protective cap protrudes through the conformal encapsulation layer.

22. A system or circuit as claimed in any preceding claim, It is characterized in that The printed circuit board is disposed close to the corresponding at least one photovoltaic cell.

23. A system or circuit as claimed in any preceding claim, It is characterized in that The printed circuit board is disposed on an insulating layer, and the insulating layer is disposed on the rear surface of the photovoltaic cell.

24. A system or circuit as claimed in any preceding claim, It is characterized in that At least one of the photovoltaic cells is arranged in an array.

25. A system or circuit as claimed in any preceding claim, It is characterized in that The planar first solar cover surface includes an optically transparent polymeric layer.

26. A method for manufacturing a solar panel, It is characterized in that The method comprises: Disposing at least one photovoltaic cell and a high-frequency power module on a first planar surface of a transparent solar cover, the at least one photovoltaic cell having a photosensitive surface facing the first planar surface of the transparent solar cover, the high-frequency power module including a high-frequency power circuit on a PC board that communicates with the at least one photovoltaic cell for collecting power from the at least one photovoltaic cell, wherein the high-frequency power circuit is disposed on a planar surface of the PC board facing away from the transparent solar cover; disposing a thermo-deformable polymeric sheet on a side of the at least one photovoltaic cell opposite the first planar surface of the transparent solar cover, the thermo-deformable polymeric sheet extending over a surface area of ​​the transparent solar cover to form a laminated stack in a plane; transferring the laminate stack to a vacuum oven; establishing a vacuum in the vacuum oven to remove air between layers of the laminate stack; heating the laminate stack to a deformation temperature of the heat-deformable polymeric sheet; applying pressure to said stack perpendicular to said plane; restoring an ambient air pressure in the vacuum oven to bond the heat-deformable polymeric sheet over the transparent solar cover and force the heat-deformable polymeric sheet to conformally bond to the at least one photovoltaic cell and the high frequency power module to form an encapsulated photovoltaic module array; and The packaged photovoltaic module array is mounted in a frame.

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