Remote sensing quantification method of atmospheric scattering radiation frequency domain characteristics

Abstract

This invention relates to the field of spectral composition measurement technology and discloses a remote sensing quantization method for the frequency domain characteristics of atmospheric scattered radiation. The method includes: inputting a modulated optical signal into a frequency domain demodulation channel and a coaxial reference channel; calculating transient fluctuations by sampling the DC component through the reference channel and dynamically calibrating the sampling window boundary; demodulating the optical signal within the sampling window based on a zero-point reference and extracting the center frequency offset and coherence bandwidth broadening; rigidly compressing the sampling window time when the input light intensity jump rate exceeds a sudden change threshold; and reconstructing discrete quantization indices using dimensionless operators. This invention breaks through the limitations of intensity spatial correction and utilizes the frequency domain phase evolution characteristics of scattered photons to achieve physical decoupling of heterogeneous spectral components, improving resolution and stability under complex operating conditions.

Description

Technical Field

[0001] This invention relates to a remote sensing quantification method for the frequency domain characteristics of atmospheric scattering radiation, belonging to the field of spectral composition measurement technology. Background Technology

[0002] Currently, in atmospheric radiative transfer and remote sensing acquisition technologies, measuring the energy distribution of spectral lines in a given band is a commonly used method. This approach typically assumes a homogeneous medium and uses a spectrometer to collect the spatial distribution of the total intensity of the incident radiation field, establishing a causal relationship between radiative energy density and target component concentration. When the light radiation field passes through a non-homogeneous medium, photons interact with medium particles, causing a random shift in the wavefront phase. Coherent light interferes and superimposes in multiple random scattering paths, leading to a decrease in spectral monochromaticity. In the frequency domain, this manifests as asymmetric broadening of the spectral profile, causing overlap of spectral components at different frequencies. In remote sensing... In high-intensity scenarios, due to the variability of the scattering medium, strong scattering interference causes frequent multi-level random scattering, resulting in asymmetric broadening and phase shift in the received spectral components. These distorted components are deeply intertwined with the target spectral components, making it impossible for spatial intensity measurement methods to accurately identify physical boundaries. Existing methods mainly focus on energy subtraction of spatial intensity and lack a demodulation mechanism for the coherent evolution characteristics of the frequency domain phase of scattered photons. This makes it impossible to separate background scattering noise from the target signal in high-dynamic environments. This deficiency leads to the measurement process relying on static approximation of empirical models for a long time. When the operating conditions change abruptly, the accumulated parameter measurement deviation causes the measurement accuracy to degrade.

[0003] To suppress scattering interference, improved approaches focus on widening the sampling bandwidth to include the complete contour, or using mechanical light-blocking devices to block the input channel of scattered light. Widening the bandwidth leads to a significant increase in thermal noise, and adding light-blocking devices restricts the acquisition field of view, failing to meet the needs of remote sensing observation. Hardware configuration improvements alone cannot overcome spatial geometric constraints, and there are also fundamental shortcomings in the demodulation control methods. For example, Chinese invention patent application CN114895319A discloses a coherent lidar that uses an optical phase-locked loop to identify complex moving targets, relying on the active Doppler frequency shift generated by the target's translational motion and utilizing a narrow... In carrier tracking mode, a bandwidth optical phase-locked loop locks a fixed reference frequency. This type of control method implicitly relies on the underlying property that the target motion law is deterministic. When faced with high dynamic conditions such as non-uniform atmospheric turbulence, random phase disturbances caused by strong scattering media, and asymmetric spectral line broadening, the technical premise is fundamentally mismatched. In addition, the lack of dual-channel underlying data interlocking and dynamic timing window truncation control mechanism makes it easy for the fixed carrier tracking loop to diverge or the phase-locked loop to lose lock when encountering non-ideal environments such as sudden cloud cover that cause sudden changes in light intensity. This makes it impossible to achieve physical decoupling of heterogeneous spectral components and suppression of crosstalk.

[0004] Therefore, the technical problem to be solved by this invention is how to use the truncation boundary of the timing sampling window of the dual-channel data interlock dynamic calibration and suppress the cumulative phase drift caused by non-uniform turbulence while using the existing processor of the system to achieve precise measurement of the target spectral components in a strong scattering background. Summary of the Invention

[0005] To address the problems in the background art, the technical solution of the present invention is as follows: A remote sensing quantization method for the frequency domain characteristics of atmospheric scattering radiation, comprising the following steps: Step S1: Obtain the aliased photoelectric carrier data stream in the multi-level atmospheric scattering background, and input the photoelectric carrier data stream in parallel to the frequency domain demodulation channel of the first spectral component and the coaxial unmodulated reference radiation reference channel. Step S2: Set the timing controller, open the timing sampling window by the timing controller, and use the first spectral component frequency domain demodulation channel to extract the root mean square value of the power spectral density residual of the photoelectric carrier data stream in the preset frequency domain within the timing sampling window, and demodulate to generate the first discrete phase coherence index. Step S3: Use the coaxial unmodulated reference radiation reference channel to sample the unmodulated transient DC component in the photoelectric carrier data stream and calculate the transient fluctuation of the transient DC component. Step S4: The transient fluctuation quantity is input from the coaxial unmodulated reference radiation reference channel to the frequency domain demodulation channel of the first spectral component in real time, and the truncation boundary of the timing sampling window is dynamically adjusted. Step S5: The first discrete phase coherence index is input in reverse from the first spectral component frequency domain demodulation channel to the coaxial unmodulated reference radiation reference channel to limit the upper limit value of the preamplifier gain. Step S6: Input the first discrete phase coherence index and the transient fluctuation quantity into the multidimensional dimensionless feature convergence operator to complete the data interleaving and fusion, and output the established discrete quantization index.

[0006] Preferably, step S4 includes the following sub-steps: Step S41, the timing controller monitors the rate of change of transient fluctuations on the time axis; Step S42, when it is determined that the rate of change of the value exceeds the set safety deviation threshold of 25%, the timing controller triggers the discrete event-driven truncation logic, compresses the duration of the timing sampling window from the initial 10μs to 2μs, and switches the operation mode to frequency domain envelope coherent tracking mode within the compressed timing sampling window, using transient fluctuations to correct the phase-locked loop integral deviation and maintain parameter convergence.

[0007] Preferably, in step S1, the parallel splitting of the photoelectric carrier data stream into the first spectral component frequency domain demodulation channel and the coaxial unmodulated reference radiation reference channel includes the following sub-steps: Step S11, using a space sensor to collect the rate of change of radiation intensity gradient in adjacent spatial quadrants, and calculating the frequency domain cutoff factor based on the rate of change of radiation intensity gradient; Step S12, inputting the frequency domain cutoff factor into the filter cutoff bandwidth input terminal of the first spectral component frequency domain demodulation channel, and limiting the response boundary of the multidimensional dimensionless feature convergence operator through spatial non-uniform working conditions.

[0008] Preferably, in step S2, extracting the root mean square value of the power spectral density residual of the photoelectric carrier data stream in the preset frequency domain includes the following sub-steps: Step S21, extracting the center frequency offset of the first spectral component frequency domain demodulation channel, and generating a phase-shifting noise reduction drive command in situ based on the center frequency offset; Step S22, applying the phase-shifting noise reduction drive command to the cascaded digital filters of the adjacent spectral component frequency domain demodulation channels that are set in parallel, and filtering the branch signals of the adjacent spectral component frequency domain demodulation channels through the cascaded digital filters.

[0009] Preferably, in step S6, inputting the first discrete phase coherence index and the transient fluctuation quantity into the multidimensional dimensionless feature convergence operator to complete data interleaving and fusion includes the following sub-steps: Step S61, collecting the first discrete phase coherence index output from the frequency domain demodulation channel of the first spectral component and the transient fluctuation quantity output from the coaxial unmodulated reference radiation reference channel to form a dynamic feature parameter set; Step S62, inputting the dynamic feature parameter set into the multidimensional dimensionless feature convergence operator for normalization convergence and weighted summation processing, and calculating the discrete quantization index through the multidimensional dimensionless feature convergence operator.

[0010] Preferably, in step S1, acquiring the aliased photoelectric carrier data stream in the multi-level atmospheric scattering background includes the following sub-steps: step S13, performing beam splitting coaxial coherent interference detection on the transmitted light and scattered light in the atmospheric detection area; step S14, generating a photoelectric signal with frequency domain modulation characteristics through multi-wavelength coaxial beam splitting interference reception, and outputting the photoelectric carrier data stream.

[0011] Preferably, in step S22, the cascaded digital filter consists of multiple stages of digital finite impulse response filters. The filtering process of the branch signals of the frequency domain demodulation channels of adjacent spectral components by the cascaded digital filter includes the following sub-steps: Step S221, changing the multiplier coefficients of the cascaded digital filter according to the phase shift noise reduction drive command; Step S222, using the cascaded digital filter with changed coefficients to perform real-time filtering of the branch signals of the frequency domain demodulation channels of adjacent spectral components to eliminate nonlinear frequency domain crosstalk.

[0012] Preferably, in step S2, the timing controller opening the timing sampling window includes the following sub-steps: Step S23, the timing controller cyclically opens and closes the timing sampling gate set at the input of the frequency domain demodulation channel of the first spectral component according to a set periodic sequence on the time axis to construct the timing sampling window; Step S24, the initial duration of the timing sampling window is set to 10μs, and the opening timing of the timing sampling window is kept in sync with the pulse radiation excitation signal received along with the photoelectric carrier data stream.

[0013] Preferably, after outputting the discrete quantization index in step S6, the following channel calibration output steps are also included: Step S63, transmitting the discrete quantization index to the multi-channel radiation spectrum calibration terminal in real time; Step S64, using the discrete quantization index to calibrate the spectral profile gain parameter in the multi-channel radiation spectrum inversion model, and completing the quantitative remote sensing quantization measurement of spectral components.

[0014] Compared with the prior art, the beneficial effects of the present invention are: 1. In the remote sensing quantization of the frequency domain characteristics of atmospheric scattered radiation, the received optical radiation field is converted into a carrier electrical signal by an optical frequency differential modulation unit. The root mean square value of the power spectral density residual of the carrier electrical signal in a specific frequency domain is extracted by discretization of the frequency domain demodulation channel of the spectral component. By utilizing the physical characteristics of the phase coherence evolution of scattered photons in the frequency domain, the asymmetric broadening distortion component caused by multi-level scattering and the effective intrinsic spectral component of the target are separated within the same sample bandwidth. This changes the traditional remote sensing quantization technology, which only uses empirical formulas to subtract in the energy intensity space. It achieves the resolution of heterogeneous spectral components without adjusting the spatial geometry, and avoids the problem of quantization accuracy deterioration caused by pseudo-spectral line aliasing under high dynamic atmospheric conditions.

[0015] 2. A strong collaborative closed loop with underlying data interlock is constructed between the spectral component frequency domain demodulation channel and the coaxial unmodulated reference radiation channel. The reference channel discretely samples the unmodulated transient DC component in the carrier electrical signal in real time and feeds it back to the demodulation channel to eliminate the cumulative phase drift introduced by atmospheric non-uniform turbulence. At the same time, the discrete phase coherence index output by the demodulation channel acts inversely on the reference channel as a rigid criterion to limit the upper limit of the preamplifier gain. This bidirectional dependent feedback adjustment topology transforms the transient fluctuations, which are traditionally regarded as noise loss, into a driving source of timing constraints through parameter interaction between the two channels, ensuring that the overall measurement process maintains parameter convergence within a long sampling period.

[0016] 3. The timing controller monitors the transient DC component variation rate of the input light intensity in real time within a specific time domain window. When the variation rate exceeds the preset 25% safety deviation threshold, it triggers the discrete event-driven hard truncation logic, rigidly compressing the window duration from the initial 10μs to 2μs. Within the truncation window, the operation mode is adaptively switched to the frequency domain envelope coherent tracking mode. This proactive feedforward mitigates the risk of phase-locked loop integral divergence and loss of lock caused by highly dynamic cloud cover or drastic airflow changes. By sacrificing some frequency resolution, it ensures the continuous convergence of the measurement channel demodulation closed loop under harsh conditions, thereby ensuring the stability and uninterrupted output of the measurement results. Attached Figure Description

[0017] Figure 1 This is a complete flowchart of the remote sensing quantification method for the frequency domain characteristics of atmospheric scattering radiation according to the present invention. Figure 2 This is a diagram illustrating the overall architecture of a remote sensing quantification method for the frequency domain characteristics of atmospheric scattering radiation according to the present invention.

[0018] The objectives, features, and advantages of this invention will be further explained in conjunction with the embodiments and with reference to the accompanying drawings. Detailed Implementation

[0019] The technical solutions of the embodiments of this application will be clearly described below with reference to the accompanying drawings. Obviously, the described embodiments are only some embodiments of this application, not all embodiments. All other embodiments obtained by those skilled in the art based on the embodiments of this application are within the scope of protection of this application.

[0020] A remote sensing quantification method for the frequency domain characteristics of atmospheric scattered radiation includes the following steps: Step S1: Obtain the aliased photoelectric carrier data stream in the multi-level atmospheric scattering background, and input the photoelectric carrier data stream in parallel to the frequency domain demodulation channel of the first spectral component and the coaxial unmodulated reference radiation reference channel. Step S2: Set the timing controller, open the timing sampling window by the timing controller, and use the first spectral component frequency domain demodulation channel to extract the root mean square value of the power spectral density residual of the photoelectric carrier data stream in the preset frequency domain within the timing sampling window, and demodulate to generate the first discrete phase coherence index. Step S3: Use the coaxial unmodulated reference radiation reference channel to sample the unmodulated transient DC component in the photoelectric carrier data stream and calculate the transient fluctuation of the transient DC component. Step S4: The transient fluctuation quantity is input from the coaxial unmodulated reference radiation reference channel to the frequency domain demodulation channel of the first spectral component in real time, and the truncation boundary of the timing sampling window is dynamically adjusted. Step S5: The first discrete phase coherence index is input in reverse from the first spectral component frequency domain demodulation channel to the coaxial unmodulated reference radiation reference channel to limit the upper limit value of the preamplifier gain. Step S6: Input the first discrete phase coherence index and the transient fluctuation quantity into the multidimensional dimensionless feature convergence operator to complete the data interleaving and fusion, and output the established discrete quantization index.

[0021] Preferably, step S4 includes the following sub-steps: Step S41, the timing controller monitors the rate of change of transient fluctuations on the time axis; Step S42, when it is determined that the rate of change of the value exceeds the set safety deviation threshold of 25%, the timing controller triggers the discrete event-driven truncation logic, compresses the duration of the timing sampling window from the initial 10μs to 2μs, and switches the operation mode to frequency domain envelope coherent tracking mode within the compressed timing sampling window, using transient fluctuations to correct the phase-locked loop integral deviation and maintain parameter convergence.

[0022] Preferably, in step S1, the parallel splitting of the photoelectric carrier data stream into the first spectral component frequency domain demodulation channel and the coaxial unmodulated reference radiation reference channel includes the following sub-steps: Step S11, using a space sensor to collect the rate of change of radiation intensity gradient in adjacent spatial quadrants, and calculating the frequency domain cutoff factor based on the rate of change of radiation intensity gradient; Step S12, inputting the frequency domain cutoff factor into the filter cutoff bandwidth input terminal of the first spectral component frequency domain demodulation channel, and limiting the response boundary of the multidimensional dimensionless feature convergence operator through spatial non-uniform working conditions.

[0023] Preferably, in step S2, extracting the root mean square value of the power spectral density residual of the photoelectric carrier data stream in the preset frequency domain includes the following sub-steps: Step S21, extracting the center frequency offset of the first spectral component frequency domain demodulation channel, and generating a phase-shifting noise reduction drive command in situ based on the center frequency offset; Step S22, applying the phase-shifting noise reduction drive command to the cascaded digital filters of the adjacent spectral component frequency domain demodulation channels that are set in parallel, and filtering the branch signals of the adjacent spectral component frequency domain demodulation channels through the cascaded digital filters.

[0024] Preferably, in step S6, inputting the first discrete phase coherence index and the transient fluctuation quantity into the multidimensional dimensionless feature convergence operator to complete data interleaving and fusion includes the following sub-steps: Step S61, collecting the first discrete phase coherence index output from the frequency domain demodulation channel of the first spectral component and the transient fluctuation quantity output from the coaxial unmodulated reference radiation reference channel to form a dynamic feature parameter set; Step S62, inputting the dynamic feature parameter set into the multidimensional dimensionless feature convergence operator for normalization convergence and weighted summation processing, and calculating the discrete quantization index through the multidimensional dimensionless feature convergence operator.

[0025] Preferably, in step S1, acquiring the aliased photoelectric carrier data stream in the multi-level atmospheric scattering background includes the following sub-steps: step S13, performing beam splitting coaxial coherent interference detection on the transmitted light and scattered light in the atmospheric detection area; step S14, generating a photoelectric signal with frequency domain modulation characteristics through multi-wavelength coaxial beam splitting interference reception, and outputting the photoelectric carrier data stream.

[0026] Preferably, in step S22, the cascaded digital filter consists of multiple stages of digital finite impulse response filters. The filtering process of the branch signals of the frequency domain demodulation channels of adjacent spectral components by the cascaded digital filter includes the following sub-steps: Step S221, changing the multiplier coefficients of the cascaded digital filter according to the phase shift noise reduction drive command; Step S222, using the cascaded digital filter with changed coefficients to perform real-time filtering of the branch signals of the frequency domain demodulation channels of adjacent spectral components to eliminate nonlinear frequency domain crosstalk.

[0027] Preferably, in step S2, the timing controller opening the timing sampling window includes the following sub-steps: Step S23, the timing controller cyclically opens and closes the timing sampling gate set at the input of the frequency domain demodulation channel of the first spectral component according to a set periodic sequence on the time axis to construct the timing sampling window; Step S24, the initial duration of the timing sampling window is set to 10μs, and the opening timing of the timing sampling window is kept in sync with the pulse radiation excitation signal received along with the photoelectric carrier data stream.

[0028] Preferably, after outputting the discrete quantization index in step S6, the following channel calibration output steps are also included: Step S63, transmitting the discrete quantization index to the multi-channel radiation spectrum calibration terminal in real time; Step S64, using the discrete quantization index to calibrate the spectral profile gain parameter in the multi-channel radiation spectrum inversion model, and completing the quantitative remote sensing quantization measurement of spectral components.

[0029] Example 1: In the field of atmospheric optical detection and radiation balance remote sensing monitoring, solar radiation undergoes multi-level non-uniform scattering when passing through the atmosphere containing aerosol particles. This results in nonlinear Doppler frequency shift and phase modulation of the photon path, producing narrow-band frequency domain distortion and asymmetric spectral broadening on both sides of the center wavelength of the target spectral components. The distortion components overlap with the intrinsic spectral components of the target in both energy space and wavelength axis, making it impossible for spatial intensity measurements to distinguish heterogeneous spectral components. The optical sensing front end emits a beam into the detection environment and applies high-frequency phase-locked sinusoidal modulation, generating initial load... The wave frequency is locked to a coherently modulated radiation field of 40.00MHz; the optical sensing front end receives the scattered radiation signal after passing through the detection environment and collects the photoelectric carrier data stream with fine spectral features; the optical sensing front end synchronously and in parallel inputs the photoelectric carrier data stream to the frequency domain demodulation channel of the first spectral component and the coaxial unmodulated reference radiation channel; the timing controller opens the timing sampling window and sets the initial duration of the timing sampling window to 10μs, so that the opening timing of the timing sampling window is synchronized with the pulse radiation excitation signal in the photoelectric carrier data stream.

[0030] The actual spectral line energy distribution obtained by performing discretized power spectral density calculation on the carrier electrical signal of the first spectral component frequency domain demodulation channel is compared with the difference sequence between the actual spectral line energy distribution and the standard intrinsic Gaussian spectral power spectral density template pre-stored in the system's static memory. The standard intrinsic Gaussian spectral power spectral density template serves as a known zero-drift reference source under scattering interference-free conditions. The specific digital processing steps for extracting the root mean square value of this residual are as follows: The power spectral density values ​​at each frequency discrete sampling node are compared point-by-point with the corresponding frequency node values ​​of the standard template. The difference is used to generate a discrete residual array covering the entire preset frequency domain; each discrete residual element in the array is squared to calculate the arithmetic mean of all squared elements; finally, the square root of the arithmetic mean is extracted to obtain the overall spectral profile distortion deviation within the sampling window, and it is directly output as the first discrete phase coherence index. The first spectral component frequency domain demodulation channel extracts the root mean square value of the power spectral density residual of the photoelectric carrier data stream in the preset frequency domain within the time-series sampling window, and demodulates to generate the first discrete phase coherence index characterizing the degree of photon scattering decoherence.

[0031] The coaxial unmodulated reference radiation channel samples the unmodulated static reference light intensity acquired coaxially, calculates the transient fluctuation of the unmodulated transient DC component in the photoelectric carrier data stream, and obtains the transient phase shift zero-point reference. The coaxial unmodulated reference radiation channel will include transient fluctuations and the zero-point reference. The input is given to the first spectral component frequency domain demodulation channel to adjust the truncation boundary of the timing sampling window. The first spectral component frequency domain demodulation channel inputs the first discrete phase coherence index to the coaxial unmodulated reference radiation channel as a criterion for limiting the upper limit of the preamplifier gain. The cumulative phase drift introduced by atmospheric non-uniform turbulence is eliminated through parameter interaction between the two channels, maintaining parameter convergence. In the cross-scale docking mechanism between the overall circuit amplitude control and the surface frequency domain phase disturbance, this limiting effect is achieved through the voltage gain inverse mapping logic inside the channel control layer. When the value of the first discrete phase coherence index increases due to the aggravation of multi-level random scattering, it characterizes the degree of decoherence of photons in atmospheric transmission. The amplitude of the demodulated useful signal rises sharply, and at this point, the amplitude of the signal will be implicitly attenuated, while the background scattering noise power will increase significantly. If the preamplifier continues to blindly maintain a high voltage gain at this time, it is very easy for the weak target signal to be overwhelmed by strong noise or to directly cause the preamplifier to experience hardware-level limiting saturation. Therefore, the central processing unit dynamically reduces the upper limit of the feedback resistor network of the digital programmable preamplifier according to the received surface phase coherence index and the preset inverse proportional mapping table. This physically and rigidly locks the overall gain upper limit of the preamplifier, avoiding overload blinding of the amplifier circuit under the continuous impact of high dynamic turbulence, and establishing a clear cross-scale control causal chain.

[0032] The timing controller monitors the rate of change of transient fluctuations on the time axis during the timing sampling window. The aforementioned 25% safety deviation threshold and 2μs cutoff duration are determined in conjunction with the theoretical extreme boundary and engineering convergence limit of photon coherence retention time under abrupt changes in highly dynamic atmospheric conditions. When the rate of change of the transient DC component reaches or exceeds 25%, it indicates that the detection area has encountered severe non-uniform airflow turbulence or abrupt cloud obstruction. At this time, the rate of change of transient phase displacement caused by multi-level scattering exceeds the inherent dynamic tracking and capture rate of traditional phase-locked loops. Under this extreme condition, the photon transient phase offset coherence retention time... The time interval will be drastically shortened to approximately 2.5 μs. To ensure that the discrete integral calculation within the timing sampling window is completed before the photon phase is completely decoherent, and based on the Nyquist sampling theorem and the minimum number of discrete data sample points required to maintain the convergence of the digital demodulation loop parameters, the system rigidly sets the maximum duration of the timing sampling window to 2 μs. This cuts off the phase drift accumulation caused by long-period sampling on the time axis, sacrificing frequency resolution to prevent the demodulation loop from losing lock under abrupt changes. When the rate of change of the numerical value exceeds the preset safety deviation threshold of 25%, the timing controller triggers the discrete event-driven truncation logic, reducing the time interval. The duration of the sequential sampling window is compressed from the initial 10μs to 2μs. During the specific execution of this frequency-domain envelope coherent tracking mode, the first spectral component frequency-domain demodulation channel disconnects the time-domain phase-locked loop integral feedback loop under conventional long-period operation, and instead adopts a fast-response digital loop based on discrete Fourier envelope estimation. Specifically, the microprocessor of the first spectral component frequency-domain demodulation channel retrieves the data values ​​of all discrete sampling points within the compressed 2μs sequential sampling window in real time, calculates the first moment of its power spectrum distribution within the processor to quickly obtain the contour envelope center frequency of the current signal, and then converts the instantaneous signal input from the coaxial unmodulated reference radiation reference channel into a real-time signal. The transient fluctuation is multiplied by a proportional damping feedforward compensation value of 0.5 and forcibly overwritten into the numerically controlled oscillator control register of the phase-locked loop (PLL). This bypasses the time-consuming integration accumulation process, achieving rigid offsetting of transient phase steps caused by strong dynamic cloud cover or drastic airflow changes. This ensures continuous locking of the spectral contour envelope and maintenance of the demodulated output within an extremely short window. The first spectral component frequency domain demodulation channel switches its operation mode to frequency domain envelope coherent tracking mode within the compressed timing sampling window. The PLL integral deviation is corrected according to the transient fluctuation, and the center frequency offset of the demodulated signal is extracted in the closed-loop convergence state to compensate for the frequency domain phase-lock loss caused by collisions. and coherent bandwidth expansion In the mode transition flow where the timing sampling window duration is rigidly compressed from the initial 10μs to 2μs, to eliminate frequency domain energy leakage and false aliasing distortion of sidelobe spectral lines caused by the hard abrupt truncation of the timing window width, the hardware control layer of the first spectral component frequency domain demodulation channel automatically applies a discrete Hanning window function weighted smoothing operator to both ends of the compressed 2μs sampling window. This operator performs a gradual sinusoidal decay of the discrete sampling point signal amplitude within 10% of the starting boundary and truncation boundary of the compressed sampling window. Zero processing is used to cut off and smoothly eliminate high-frequency digital harmonic components and phase jump artifacts caused by hard truncation of the rectangular window. This technique maintains the monotonic convergence of the closed-loop demodulation system's reference parameters while offsetting the negative energy diffusion caused by the shortening of the time-domain window for fine demodulation of the spectral profile. This ensures the physical accuracy of the subsequently extracted center frequency offset and coherence bandwidth broadening, and eliminates system operation conflicts within the state change dead zone. The quantization unit collects the first discrete phase coherence index and center frequency offset output from the first spectral component frequency domain demodulation channel. and coherent bandwidth expansion A dynamic feature parameter set is formed, and this set is input into a multidimensional dimensionless feature convergence operator for normalization and weighted summation. The output is the established discrete quantization index. The operation of the multidimensional dimensionless feature convergence operator satisfies the following relation: ,in, This is a quantitative index for the frequency domain characteristics of the output atmospheric scattered radiation. This is a preset atmospheric attenuation correction factor with a fixed value of 1.26. This is the center frequency offset of the beat frequency signal. This refers to the amount of coherent bandwidth expansion. The reference frequency for high-frequency phase-locked loop (PLL) sinusoidal modulation is fixed at 40.00 MHz. In the specific operator data interleaving process, the first discrete phase coherence index and transient fluctuation amount together serve as the weight control kernel and boundary physical constraint for demodulation feature extraction. Specifically, the center frequency offset of the beat frequency signal is calculated by performing discretized differential integration on the aliased optoelectronic carrier data stream in the preset frequency domain, using the transient fluctuation amount output by the coaxial unmodulated reference radiation reference channel as a dynamic step size correction factor, under the convergence state of the PLL. This seamlessly integrates the transient phase disturbance in the time domain. The mapping is a defined center frequency shift; the coherence bandwidth broadening is obtained by substituting the root mean square value of the demodulated optical power spectral density residual into the asymmetric Gaussian envelope fitting model of the spectral line network, and using the first discrete phase coherence index as the scaling product weight of the envelope broadening boundary to extract the full width at half maximum of the power spectral density. Thus, the center frequency shift and coherence bandwidth broadening in the operator formula fully include the underlying physical contributions of the first discrete phase coherence index and transient fluctuations, realizing the normalization mapping and dimensionality reduction convergence of the input parameters to the frequency domain physical feature dimension.

[0033] Space sensors collect the rate of change of radiation intensity gradient in adjacent spatial quadrants. According to the rate of change of radiation intensity gradient Calculate the frequency domain cutoff factor Their relationship satisfies ,in, It is the frequency domain cutoff factor. The rate of change of radiation intensity gradient, The spatial harmonic coefficient is fixed at 0.45; the first spectral component frequency domain demodulation channel receiving frequency domain cutoff factor. The response boundary of the multidimensional dimensionless feature convergence operator is constrained by the spatial non-uniform working condition; the frequency domain compensation unit extracts the center frequency offset of the current channel. According to the center frequency offset The output phase-shift noise reduction drive command is applied to the cascaded digital filters of the adjacent spectral component frequency domain demodulation channels, which are set up in parallel. The cascaded digital filters change the multiplier coefficients of the multi-stage digital finite impulse response filters according to the phase-shift noise reduction drive command, filtering the branch signals of the adjacent spectral component frequency domain demodulation channels and erasing parasitic aliasing frequency components caused by nonlinear interactions. Their relationship satisfies ,in, For parasitic aliasing frequency components, This is the center frequency offset. Using the reference frequency, the overlapping interference of nonlinear frequency domain crosstalk components and adjacent spectral components in the frequency domain is eliminated. The quantization unit transmits the calculated discrete quantization index to the multi-channel radiation spectral calibration terminal in real time. The multi-channel radiation spectral calibration terminal calibrates the spectral profile gain parameters in the multi-channel radiation spectral inversion model according to the discrete quantization index. This allows the entire spectral measurement system to complete the quantitative remote sensing quantization measurement of spectral components through local spectral frequency domain feature demodulation and discrete decoupling rules without the constraint of external physical obstruction devices. It separates the multi-level scattering broadening components from the effective target spectral components, suppresses background scattering noise in the detection environment, and analyzes the profile features of the target spectral components.

[0034] Example 2: When the system faces a closed aerodynamic experimental chamber environment with non-uniform aerosol particles, the spectral resolution of the optical sensing front end is determined to be 0.01 nm, the sampling rate of the photoelectric acquisition unit is locked at 100 MHz, and the optical sensing front end emits a coherent laser beam into the closed aerodynamic experimental chamber environment to acquire photoelectric carrier data streams containing multi-level scattering characteristics, thus establishing the physical acquisition source and functional specification boundary of the experimental data. Since the initial duration of the time-series sampling window directly affects the resolution accuracy of the narrowband spectral components, its value is controlled by the atmospheric turbulence coherence retention time and frequency domain integration accuracy requirements. When the high-frequency turbulence activity in the detection environment weakens and the local photon coherence retention time is extended, in order to increase the number of discrete integration points of the first spectral component frequency domain demodulation channel within the time-series sampling window and improve the spectral quantization fineness, the duration of the time-series sampling window is moved towards the upper limit of the value range. Under the specific aerosol mass concentration distribution conditions of the closed aerodynamic experimental chamber, the initial duration of the time-series sampling window is determined to be 10 μs based on the monotonically increasing relationship between the duration of the time-series sampling window and the photon coherence retention time.

[0035] Aerosol particle swarms of different mass concentrations were introduced into a sealed aerodynamic experimental chamber to establish an intensity gradient control system encompassing low, medium, and high challenge intensity conditions. The transient rate of input light intensity variation corresponding to the low challenge intensity condition was 15.34 W / (m²·s), the medium challenge intensity condition was 32.16 W / (m²·s), and the high challenge intensity condition was 65.42 W / (m²·s). Furthermore, the initial carrier frequency of the photoelectric carrier data stream in each test group using the method of this invention was fixed at 40.00 MHz. Under the low challenge intensity condition, the center frequency offset of the demodulated beat frequency signal extracted by the test group using the method of this invention was... The measured value is 1.23 kHz, and the coherence bandwidth broadening is... The measured value is 4.56 kHz. The calculated output is the quantized index of the frequency domain characteristics of atmospheric scattered radiation. The measured value was 0.08, the spectral quantization error was 2.11%, and the center frequency shift extracted by the test group using the method of this invention under medium-challenge intensity conditions was [value missing]. The measured value is 2.45 kHz, and the coherence bandwidth broadening is... The measured value is 8.92 kHz. The calculated output is the quantization index of the frequency domain characteristics of atmospheric scattered radiation. The measured value was 0.14, and the spectral quantization error was 2.43%. Under high-intensity working conditions, the test group using the method of this invention extracted the center frequency shift. The measured value is 3.12 kHz, and the coherence bandwidth broadening is... The measured value is 12.14 kHz. The calculated output is the quantization index of the frequency domain characteristics of atmospheric scattered radiation. The measured value was 0.20, the spectral quantization error was 3.25%, and all parameters maintained a monotonically convergent state within the intensity gradient. Under the same other process conditions, as the first control group (with the coaxial unmodulated reference radiation channel feedback adjustment mechanism removed), the center frequency shift under low-challenge intensity conditions was [data missing]. The measured value was 0.54 kHz, the spectral quantization error increased to 8.45%, and the center frequency shift under medium-challenging conditions was [missing information]. The measured value was 5.67 kHz, the spectral quantization error increased to 14.23%, and the center frequency shift under high-challenge conditions was significant. The measured value was 9.12 kHz, and the spectral quantization error increased to 22.16%. The deviation between the test group and control group 1 using the method of this invention confirms the system-level synergistic effect of dual-channel parameter interaction in eliminating turbulent phase drift. As a second control group, in control group 2, which kept the duration of the timing sampling window constant at 10 μs and removed the timing truncation logic, the spectral quantization error was 2.15% under low-challenge intensity conditions and 2.51% under medium-challenge intensity conditions. However, under high-challenge intensity conditions, due to the input light intensity jump rate reaching 65.42 W / (m²·s) and exceeding the preset safety deviation threshold of 25%, the wide sampling window of static sampling caused phase-locked loop loss, resulting in an output center frequency offset. The introduction of noise signals increased the spectral quantization error to 68.54%, leading to measurement interruption. The stability of adaptive timing truncation control in mitigating lock-up losses under dynamic abrupt changes was confirmed by the state mutation of the test group and control group II using the method of this invention under high-challenge conditions. As a third control group, in control group III where the safety deviation threshold was lowered to 12%, the input light intensity change rate prematurely met the change rate judgment condition under medium-challenge conditions, rigidly compressing the sampling window duration to 2 μs. Due to insufficient frequency domain discrete integral length, the spectral resolution decreased. The spectral quantization error increased to 7.89%. As the fourth control group, the control group four, in which the safety deviation threshold was raised to 45%, under medium-challenge conditions, due to the failure to meet the cutoff condition and the continuous maintenance of a sampling time of 10μs, the phase-locked loop was subjected to continuous turbulent impacts and approached the upper limit of the amplification gain, resulting in decoherent response deviation. The spectral quantization error increased to 19.87%. The parameter variation trends of control groups three and four showed nonlinear performance inflection points, confirming that the 25% numerical boundary is the optimal working window that balances narrowband resolution and system stability.

[0036] The quantization unit outputs the first discrete phase coherence index and center frequency offset from the frequency domain demodulation channel of the first spectral component. and coherent bandwidth expansion The parameters are combined into a dynamic feature parameter set, which is then input into a multidimensional dimensionless feature convergence operator for normalization and weighted summation. The output is a discrete quantization index. The operation of the multidimensional dimensionless feature convergence operator satisfies the following relation: ,in, This is a quantitative index for the frequency domain characteristics of the output atmospheric scattered radiation. This is a preset atmospheric attenuation correction factor with a fixed value of 1.26. This is the center frequency offset of the beat frequency signal. This refers to the amount of coherent bandwidth expansion. The reference frequency for high-frequency phase-locked sinusoidal modulation is fixed at 40.00 MHz. The space sensor collects the rate of change of radiation intensity gradient between adjacent spatial quadrants. According to the rate of change of radiation intensity gradient Calculate the frequency domain cutoff factor Its operations satisfy the following relation: ,in, It is the frequency domain cutoff factor. It is the spatial harmonic coefficient, and its value is fixed at 0.45. The radiation intensity gradient change rate; the first spectral component frequency domain demodulation channel receiving frequency domain cutoff factor. The response boundary of the multidimensional dimensionless feature convergence operator is constrained by the spatial non-uniform working condition; the frequency domain compensation unit extracts the center frequency offset of the current channel. According to the center frequency offset The output phase-shift noise reduction drive command is applied to the cascaded digital filters of the adjacent spectral component frequency domain demodulation channels, which are set up in parallel. The cascaded digital filters change the multiplier coefficients of the multi-stage digital finite impulse response filters according to the phase-shift noise reduction drive command, thereby filtering the branch signals of the adjacent spectral component frequency domain demodulation channels and erasing parasitic aliasing frequency components caused by nonlinear interactions. Its operations satisfy the following relation: ,in, For parasitic aliasing frequency components, This is the center frequency offset. Using a reference frequency fixed at 40.00MHz, the system eliminates crosstalk between channels and overlapping interference between adjacent spectral components in the frequency domain. The quantization unit transmits the calculated discrete quantization index to the multi-channel radiation spectral calibration terminal in real time. The multi-channel radiation spectral calibration terminal then corrects the spectral profile gain parameters in the multi-channel radiation spectral inversion model based on the discrete quantization index. This allows the entire spectral measurement system to perform quantitative remote sensing quantization of spectral components through local spectral frequency domain feature demodulation and discrete decoupling rules, without the need for external physical obstructions. This separates multi-level scattering broadening components from the effective target spectral components, suppresses background scattering noise in the detection environment, and analyzes the profile features of the target spectral components.

[0037] Example 3: This example combines Figures 1 to 2 This section describes a remote sensing quantization method for the frequency domain characteristics of atmospheric scattering radiation, such as... Figure 1As shown in the figure, this diagram presents the specific steps of a remote sensing quantization method for atmospheric scattering radiation frequency domain characteristics, including the flow connections between steps S1, S2, S3, S4, S5, and S6. Step S1 involves acquiring the aliased photoelectric carrier data stream in a multi-level atmospheric scattering background, and inputting the photoelectric carrier data stream in parallel to the first spectral component frequency domain demodulation channel and the coaxial unmodulated reference radiation channel. Step S2 involves setting the timing controller to open the timing sampling window, and using the first spectral component frequency domain demodulation channel to extract the root mean square value of the power spectral density residual of the photoelectric carrier data stream in the preset frequency domain within the timing sampling window, demodulating to generate the first discrete phase coherence index. Step S3 involves... The unmodulated transient DC component in the optoelectronic carrier data stream is sampled using a coaxial unmodulated reference radiation reference channel, and the transient fluctuation of the transient DC component is calculated. Step S4 is to input the transient fluctuation from the coaxial unmodulated reference radiation reference channel to the first spectral component frequency domain demodulation channel in real time, and dynamically adjust the truncation boundary of the timing sampling window. Step S5 is to input the first discrete phase coherence index from the first spectral component frequency domain demodulation channel in reverse to the coaxial unmodulated reference radiation reference channel, and limit the upper limit value of the preamplifier gain. Step S6 is to input the first discrete phase coherence index and the transient fluctuation together into the multidimensional dimensionless feature convergence operator to complete the data interleaving and fusion, and output the established discrete quantization index.

[0038] like Figure 2As shown, the overall architecture of the implementation method is fully demonstrated, which includes a space sensor, a coaxial unmodulated reference radiation channel, an optical sensing front-end, a first spectral component frequency domain demodulation channel, a timing controller, a timing bias increment register, a multi-level discrete register, a frequency domain decoupling and data convergence core, a multi-dimensional dimensionless feature convergence operator, a multi-channel radiation spectrum calibration terminal, a quantization unit, a multi-channel radiation spectrum inversion model, a frequency domain compensation unit, a cascaded digital filter, and a multi-level digital finite impulse response filter. The space sensor is connected to the first spectral component frequency domain demodulation channel. The optical sensing front-end is connected to both the coaxial unmodulated reference radiation channel and the first spectral component frequency domain demodulation channel. In the left-hand chain, the coaxial unmodulated reference radiation channel is sequentially connected in series to the timing controller, the timing bias increment register, and the multi-level discrete register. The multi-level discrete register is further connected to the frequency domain decoupling and data convergence core. Inside the convergence core, the multidimensional dimensionless feature convergence operator is located in the right-hand chain. The first spectral component frequency domain demodulation channel is sequentially connected in series to the frequency domain compensation unit, the cascaded digital filter, and the multi-stage digital finite impulse response filter. The multi-stage digital finite impulse response filter is connected to the multidimensional dimensionless feature convergence operator. In the central processing architecture, the multidimensional dimensionless feature convergence operator and the multi-channel radiation spectral calibration terminal are located inside the physical frame of the frequency domain decoupling and data convergence core and are connected in series from top to bottom. The output of the multi-channel radiation spectral calibration terminal extends downward to the quantization unit below the frequency domain decoupling and data convergence core. The quantization unit is further connected downward to the multi-channel radiation spectral inversion model. In addition, a closed-loop dashed feedback line is set on the right side of the overall architecture. This dashed feedback line is led out from the right side of the quantization unit, extends upward as a broken line, and finally points horizontally to the right input of the multidimensional dimensionless feature convergence operator.

[0039] Example 4: In the field of atmospheric optical detection and radiation balance remote sensing monitoring, the long-term continuous operation of the optical sensing front end causes nonlinear zero-point drift at the hardware level due to the accumulation of thermal noise in the detector components over time and the selective degradation of photoelectric transduction efficiency. This results in an asymmetric micro-displacement of the static physical registration boundary between the first spectral component frequency domain demodulation channel and the coaxial unmodulated reference radiation channel. When the two channels process the photoelectric carrier data stream in parallel, a dynamic phase imbalance component is introduced, causing the timing controller to generate an intrinsic timing delay when determining the same frequency synchronization, resulting in a shift in the calculated center frequency of the output. This deviates from its actual physical quantization range, resulting in a long-term cumulative bias that reduces the monotonic convergence strength of the data.

[0040] To offset the timing delay caused by asymmetric micro-displacements, the remote sensing quantization method introduces a parameter in the timing determination process to compensate for the non-uniform degradation of gain and phase between channels. This parameter is defined as the frequency domain unbalanced coherence factor. This method eliminates the inherent technical deficiency of lacking data support by using the standard deviation of the transient fluctuation of the static reference light intensity acquired by the reference channel within a sliding time-domain window as the boundary deviation, and calculating the ratio of the standard deviation to the preset coherent sampling reference voltage in the frequency domain demodulation channel of the first spectral component to determine the specific value. In the specific technical implementation, the timing controller includes multi-level discrete registers, and its processing steps are determined as follows: retrieve the transient fluctuation sequence of the coaxial unmodulated reference radiation reference channel within 5 consecutive sliding sampling windows; calculate the standard deviation of the sequence inside the processor to obtain a voltage deviation standard deviation term with a value of 0.15V; calculate the voltage deviation standard deviation term and the coherent sampling reference voltage fixed at 0.12V by division to output the frequency domain unbalanced coherence factor. The specific value is 1.25; the timing controller will adjust the frequency domain unbalanced coherence factor. As a feedback input, it acts on the timing adjustment circuit of the timing sampling window to correct the pulse triggering front edge of the timing sampling window, so that the opening time of the timing sampling window is forward by 12ns to offset the delay lag loss caused by component degradation, and restore the underlying data interlocking closed loop of the dual channels without changing the external hardware topology.

[0041] Frequency domain unbalanced coherence factor The modified relation of the multidimensional dimensionless feature convergence operator involved satisfies the following relation: ,in, This is a quantitative index for the frequency domain characteristics of the output atmospheric scattered radiation. The frequency domain unbalanced coherence factor used to offset channel variations has a computational value of 1.25 under the current operating conditions. This is a preset atmospheric attenuation correction factor with a fixed value of 1.26. This is the center frequency offset of the beat frequency signal. This refers to the amount of coherent bandwidth expansion. The reference frequency for high-frequency phase-locked sinusoidal modulation is fixed at 40.00 MHz, after passing through the frequency domain unbalanced coherence factor. Timing calibration and operator correction are performed to suppress cross-channel signal delay and transient phase shift caused by component variations, thereby enabling the quantization of atmospheric scattering radiation frequency domain characteristics output by the multidimensional dimensionless feature convergence operator. The calculation results maintain a stable output state of monotonic self-calibration under high dynamic medium attenuation interference, thereby constraining the multi-channel radiation spectrum inversion model from the negative interference of component drift. As a result, the demodulation accuracy of the remote sensing quantitative measurement process can be maintained within the original design index range for a long time without adjusting the external hardware configuration.

[0042] Example 5: When the system faces its first field deployment, in order to eliminate the initial coherent bias obstacle introduced by the difference in intrinsic optical detection background between different remote sensing sites, the optical sensing front end emits a standard modulated radiation field with a carrier frequency fixed at 40.00MHz into the standard reference channel composed of standard blocks with known transmittance. The coaxial unmodulated reference radiation reference channel acquires the static waveform data transmitted through the standard reference channel and calculates the initial phase bias. The timing controller will set the initial phase offset. Write to the timing offset increment register to lock the initial position of the relative sampling offset of the pulsed radiation excitation signal at a fixed time node of 0.12ns, eliminating the initial timing alignment error caused by the inherent length difference of the signal transmission cable, thereby reconstructing the bias-free physical measurement channel reference before officially starting atmospheric scattering detection.

[0043] Within a pressure-controlled test chamber containing a standard transparent nitrogen medium, the system uses a standard modulated radiation field to calibrate the second-order energy dissipation residual generated by the high-frequency phase-locked sinusoidal modulation itself. The first spectral component frequency domain demodulation channel discretely measures the reference phase coherence index under pure scattering conditions. The inherent electrical frequency loss constant is calculated by a cascaded digital filter through multipliers in the demodulation channel. Its operations satisfy the following relation: ,in, The inherent electrical frequency loss constant was calculated, and its measured value in the voltage-controlled test chamber is 0.05 kHz. This is the initial phase offset. To obtain the transient phase shift zero-point reference, The reference frequency for high-frequency phase-locked sinusoidal modulation is fixed at 40.00 MHz. To eliminate the dimensional mismatch between the surface time difference and the overall frequency unit at the operator-level operation, the final frequency unit output of the aforementioned inherent electrical frequency loss constant is achieved through a preset unit normalization coefficient within the system. Specifically, the dimensionless pulse count ratio obtained by multiplying the initial phase offset by the reference frequency of high-frequency phase-locked sinusoidal modulation essentially characterizes the proportion of timing alignment misalignment introduced by the inherent cable length difference in the hardware acquisition channel. The system executes... When this ratio is divided by the transient phase shift zero-point reference, the dimensionless calculation result is automatically multiplied by a 1kHz standard reference frequency scalar. This seamlessly bridges the surface time delay and phase offset into a holistic frequency loss characteristic, giving the calculated electrical frequency loss constant a clear frequency dimension. Its magnitude directly corresponds to the equivalent nonlinear frequency drift component caused by hardware signal delay within a 1-second period, ensuring its physical dimensional consistency during subsequent zero-point correction of the multidimensional dimensionless feature convergence operator. The quantization unit then converts the inherent electrical frequency loss constant... The values ​​are imported into the system's underlying layer by directly rewriting the cell address of the multi-channel radiation spectral calibration terminal storage matrix, constraining the zero-point correction parameters of the multidimensional dimensionless feature convergence operator, and completing the pre-zero bias cleaning of the spectral component remote sensing detection path.

[0044] It will be apparent to those skilled in the art that the present invention is not limited to the details of the exemplary embodiments described above, and that the present invention can be implemented in other specific forms without departing from the spirit or essential characteristics of the present invention.

[0045] Finally, it should be noted that the above embodiments are only used to illustrate the technical solutions of the present invention and are not intended to limit it. Although the present invention has been described in detail with reference to preferred embodiments, those skilled in the art should understand that modifications or equivalent substitutions can be made to the technical solutions of the present invention without departing from the spirit and scope of the technical solutions of the present invention.

Claims

1. A remote sensing quantization method for the frequency domain characteristics of atmospheric scattered radiation, characterized in that, Includes the following steps: Step S1: Obtain the aliased photoelectric carrier data stream in the multi-level atmospheric scattering background, and input the photoelectric carrier data stream in parallel to the frequency domain demodulation channel of the first spectral component and the coaxial unmodulated reference radiation reference channel. Step S2: Set the timing controller, open the timing sampling window by the timing controller, and use the first spectral component frequency domain demodulation channel to extract the root mean square value of the power spectral density residual of the photoelectric carrier data stream in the preset frequency domain within the timing sampling window, and demodulate to generate the first discrete phase coherence index. Step S3: Use the coaxial unmodulated reference radiation reference channel to sample the unmodulated transient DC component in the photoelectric carrier data stream and calculate the transient fluctuation of the transient DC component. Step S4: The transient fluctuation quantity is input from the coaxial unmodulated reference radiation reference channel to the frequency domain demodulation channel of the first spectral component in real time, and the truncation boundary of the timing sampling window is dynamically adjusted. Step S5: The first discrete phase coherence index is input in reverse from the first spectral component frequency domain demodulation channel to the coaxial unmodulated reference radiation reference channel to limit the upper limit value of the preamplifier gain. Step S6: Input the first discrete phase coherence index and the transient fluctuation quantity into the multidimensional dimensionless feature convergence operator to complete the data interleaving and fusion, and output the established discrete quantization index.

2. The remote sensing quantization method for the frequency domain characteristics of atmospheric scattering radiation according to claim 1, characterized in that, Step S4 includes the following sub-steps: Step S41, the timing controller monitors the rate of change of transient fluctuations on the time axis; Step S42, when it is determined that the rate of change of the value exceeds the set safety deviation threshold of 25%, the timing controller triggers the discrete event-driven truncation logic, compresses the duration of the timing sampling window from the initial 10μs to 2μs, and switches the operation mode to frequency domain envelope coherent tracking mode within the compressed timing sampling window, using transient fluctuations to correct the phase-locked loop integral deviation and maintain parameter convergence.

3. The remote sensing quantization method for the frequency domain characteristics of atmospheric scattering radiation according to claim 1, characterized in that, In step S1, the parallel splitting of the photoelectric carrier data stream into the first spectral component frequency domain demodulation channel and the coaxial unmodulated reference radiation reference channel includes the following sub-steps: Step S11, using a space sensor to collect the rate of change of radiation intensity gradient in adjacent spatial quadrants, and calculating the frequency domain cutoff factor based on the rate of change of radiation intensity gradient; Step S12, inputting the frequency domain cutoff factor into the filter cutoff bandwidth input of the first spectral component frequency domain demodulation channel, and limiting the response boundary of the multidimensional dimensionless feature convergence operator through spatial non-uniform working conditions.

4. The remote sensing quantization method for the frequency domain characteristics of atmospheric scattering radiation according to claim 1, characterized in that, In step S2, extracting the root mean square value of the power spectral density residual of the photoelectric carrier data stream in the preset frequency domain includes the following sub-steps: Step S21, extracting the center frequency offset of the first spectral component frequency domain demodulation channel, and generating a phase-shifting noise reduction drive command in situ based on the center frequency offset; Step S22, applying the phase-shifting noise reduction drive command to the cascaded digital filters of the adjacent spectral component frequency domain demodulation channels that are set in parallel, and filtering the branch signals of the adjacent spectral component frequency domain demodulation channels through the cascaded digital filters.

5. The remote sensing quantization method for the frequency domain characteristics of atmospheric scattering radiation according to claim 1, characterized in that, In step S6, the first discrete phase coherence index and the transient fluctuation quantity are jointly input into the multidimensional dimensionless feature convergence operator to complete the data interleaving and fusion, which includes the following sub-steps: Step S61, collect the first discrete phase coherence index output by the frequency domain demodulation channel of the first spectral component and the transient fluctuation quantity output by the coaxial unmodulated reference radiation reference channel to form a dynamic feature parameter group; Step S62: Input the dynamic feature parameter set into the multidimensional dimensionless feature convergence operator for normalization convergence and weighted summation processing, and calculate the discrete quantization index through the multidimensional dimensionless feature convergence operator.

6. The remote sensing quantization method for the frequency domain characteristics of atmospheric scattered radiation according to claim 1, characterized in that, In step S1, acquiring the aliased photoelectric carrier data stream in the multi-level atmospheric scattering background includes the following sub-steps: Step S13, performing beam splitting coaxial coherent interference detection on the transmitted light and scattered light in the atmospheric detection area; Step S14, generating a photoelectric signal with frequency domain modulation characteristics through multi-wavelength coaxial beam splitting interference reception, and outputting the photoelectric carrier data stream.

7. The remote sensing quantization method for the frequency domain characteristics of atmospheric scattering radiation according to claim 4, characterized in that, In step S22, the cascaded digital filter consists of multiple stages of digital finite impulse response filters. The filtering of the branch signals of the frequency domain demodulation channels of adjacent spectral components by the cascaded digital filter includes the following sub-steps: Step S221, changing the multiplier coefficients of the cascaded digital filter according to the phase shift noise reduction drive command; Step S222, using the cascaded digital filter with changed coefficients to perform real-time filtering of the branch signals of the frequency domain demodulation channels of adjacent spectral components to eliminate nonlinear frequency domain crosstalk.

8. The remote sensing quantization method for the frequency domain characteristics of atmospheric scattering radiation according to claim 1, characterized in that, In step S2, opening the timing sampling window by the timing controller includes the following sub-steps: Step S23, the timing controller cyclically opens and closes the timing sampling gate set at the input end of the frequency domain demodulation channel of the first spectral component according to the set period sequence on the time axis to construct the timing sampling window; Step S24: Set the initial duration of the timing sampling window to 10 μs, and keep the opening timing of the timing sampling window synchronized with the pulse radiation excitation signal received along with the photoelectric carrier data stream.

9. The remote sensing quantization method for the frequency domain characteristics of atmospheric scattering radiation according to claim 1, characterized in that, After outputting the discrete quantization index in step S6, the following channel calibration output steps are also included: Step S63, the discrete quantization index is transmitted to the multi-channel radiation spectrum calibration terminal in real time; Step S64, the discrete quantization index is used to calibrate the spectral profile gain parameter in the multi-channel radiation spectrum inversion model to complete the quantitative remote sensing quantization measurement of spectral components.

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