LED RAPID ACTIVATION SYSTEM

Description

TECHNICAL FIELD

[0001] The present invention relates to an LED quick activation system, and more particularly, to an LED quick activation system capable of rapidly charging its filter capacitor and being substantially free from feedback voltage detection.BACKGROUND

[0002] As technology develops and white LED (Light Emitting Diode) comes out with a breakthrough, LEDs have been applied on various types of household appliances. On top of that, since LEDs' high efficiency in illumination, they are replacing conventional incandescent lamps and fluorescent lamps in the market.

[0003] For improving a conventional LED unit's illuminating stability, the conventional LED unit is mounted with a capacitor that has a large capacitance at its driving circuit's output stage. Therefore, while under a low luminance (i.e., a low-amplitude current), the conventional LED's driving circuit will take too long a period to illuminate itself because of its capacitor's large capacitance. And it is highly likely to mislead its user that said conventional LED unit is malfunctioning. As a matter of fact, the conventional LED unit's operational voltage characteristics are the actual factor of the long activation period. Specifically, before the capacitor charges itself for successfully activating the conventional LED unit, the conventional LED unit has been overpowered but its operational voltage still stays within its cutoff zone, such that said conventional LED unit cannot rapidly activate itself under such a condition.

[0004] CN-A-102510619 discloses a quick start-up device of an LED (light-emitting diode) driving power supply. The quick start-up device comprises a bias circuit, a power supply circuit and a control unit, wherein the bias circuit comprises a starting resistor and a driving capacitor, and provides a grid bias voltage for a power switch tube of the power supply circuit; the power supply circuit comprises the power switch tube, a switch device and a power supply capacitor, and the power supply capacitor provides a working current and a working voltage for the control unit; and during the starting process of the control unit, the switch device is started up, thus current passes through the power switch tube and the switch device, and the power supply capacitor is charged quickly, thus the quick start-up of the LED driving power supply is realized.SUMMARY

[0005] The present invention is defined in the appended claims and is directed to a light-emitting diode (LED) quick activation system, the LED quick activation system includes: a driving circuit which is configured to generate an output driving voltage and a driving current using a received power; a loading module which is electrically coupled to the driving circuit, and configured to illuminate its LED unit using the output driving voltage and the driving current; a filter capacitor which is electrically coupled to the loading module in parallel, and is configured to charge its cross voltage using the output driving voltage or discharge its cross voltage to ground; a current control switch which is electrically coupled to the driving circuit configured for receiving the driving current, and is configured to control input power to the loading module and the filter capacitor; a quick discharging module which is electrically coupled to the loading module and the filter capacitor in parallel, and is configured to discharge the filter capacitor to the ground; and characterized in that, the LED quick activation system further includes a primary controller electrically coupled to the driving circuit, the current control switch and the quick discharging module, wherein the primary controller is configured to: store a discharging parameter calculated during a period that the quick discharging module discharges the filter capacitor, calculate an equivalent charging time period for charging the filter capacitor's cross voltage to a target charging voltage using the discharging parameter, control the current control switch to charge the filter capacitor and the loading module using the driving current of a charging amplitude during the equivalent charging period, and charge the filter capacitor and the loading module using the driving current of a regular amplitude after the equivalent charging period passes; wherein the equivalent charging period is a sum of a discharging period (T_Ron) and a charging period (T_Roff) of the filter capacitor, and wherein the target charging voltage refers to a lower-bound voltage that charges the filter capacitor to the extent that the loading module normally operates in a significantly short period; wherein the quick discharging module includes: a first controller which is electrically coupled to the driving circuit for receiving the output driving voltage; a second controller which is electrically coupled to the filter capacitor's output terminal configured for detecting the filter capacitor's cross voltage; a logic gate, which is respectively and electrically coupled to the first controller and the second controller, configured for receiving respective output control signals; a counter, electrically coupled in between the first controller and the logic gate; and a discharging unit which is electrically coupled to the loading module in parallel; wherein the first controller is further configured to compare the output driving voltage with the target charging voltage; wherein when the output driving voltage of the driving circuit is higher than the target charging voltage, the first controller is further configured to output a high-level voltage to the counter, and the counter is further configured to in turn keep on resetting the counter's count and output a first logic parameter that corresponds to the high-level voltage to the logic gate's first input terminal; wherein the second controller is further configured to sense the filter capacitor's cross voltage that exceeds the target charging voltage, and correspondingly generate a second logic parameter that corresponds to the filter capacitor's cross voltage to the logic gate's second input terminal; and wherein the logic gate is further configured to perform a logic calculation on both the first logic parameter and the second logic parameter to keep the discharging unit open-circuit, such that the output driving voltage keeps on charging the filter capacitor and the loading module; wherein the first controller is further configured to compare the output driving voltage with the target charging voltage; wherein when the output driving voltage of the driving circuit is lower than the target charging voltage, the first controller is further configured to output a low-level voltage to the counter; wherein the counter is further configured to in turn accumulate its count as a clock, and is further configured to output a third logic parameter to the logic gate's first input terminal; wherein during the counter's count accumulation the filter capacitor begins discharging its cross voltage, such that the second controller still senses the filter capacitor's cross voltage and correspondingly generates the second logic parameter; wherein the logic gate is further configured to perform a logic calculation on both the third logic parameter and the second logic parameter, and to in turn activate the discharging unit and wherein when the discharging unit is activated, the discharging unit discharges the filter capacitor to a ground level, and the primary controller is further configured to store the counter's final count as the discharging parameter; wherein the current control switch includes a constant resistor and a corresponding transistor; wherein the primary controller is further configured to calculate the target charging voltage as: V_target=V_C×X; wherein V_target represents the target charging voltage, V_C represents the loading module's LED barrier voltage, and X represents a charging end ratio; wherein the primary controller is further configured to calculate the discharging period of the filter capacitor as: T_Ron=S_th / F_sw =M; wherein T_Ron and M represent the discharging period, S_th represents the counter's final count, and F_sw represents a power transformation switch frequency; wherein the primary controller is further configured to calculate a charging voltage that the filter capacitor (CF)'s cross voltage reaches during the same period as the discharging period as: V_(C, TRon)=(I_in×M / C) / (1+M / RC); wherein V_(C, TRon) represents the charging voltage, M represents the discharging period, I_in represents the driving current from the driving circuit, C represents the filter capacitor's capacitance, and R represents the constant resistor's resistance; wherein the primary controller is further configured to calculate a charging period, during which the charging voltage takes to charge till reaching the target charging voltage, as: T_Roff=(V_target-V_(C, TRon) )×I_in / C; wherein T_Roff i represents the charging period, V_(C, TRon) represents the charging voltage, V_target represents the target charging voltage, I_in represents the driving current from the driving circuit, and C represents the filter capacitor's capacitance.

[0006] In one example, the primary controller is implemented using at least one or a combination of a CPU, a programmable unit microprocessor for general use or specific use, a digital signal processor, and an application specific integrated circuit.

[0007] In one example, the primary controller further includes a storage unit for permanently or quasi-permanently storing information that includes a lookup table or multiple sets of operating parameters or pre-storing operating parameters.BRIEF DESCRIPTION OF THE DRAWINGS

[0008] FIG. 1 illustrates a schematic diagram of a LED quick activation system according to one embodiment. FIG. 2 illustrates a detailed diagram of how FIG. 1's LED quick activation system's quick discharging module interacts with the LED quick activation system's driving circuit, filter capacitor and loading module according to one example. FIG. 3 and FIG. 4 illustrate equivalent circuit diagrams of how FIG. 1's LED quick activation system's controller determines a discharging parameter. FIG. 5 illustrates a flowchart of a quick activation method that the LED quick activation system shown in FIG. 1 applies according to one embodiment. DETAILED DESCRIPTION OF THE EMBODIMENTS

[0009] As mentioned above, the present disclosure discloses a LED quick activating system for substantially neutralizing the conventional LED unit's defect in its capacitor's long charge period. Specifically, the disclosed LED quick activating system is capable of rapidly charging its filter capacitor under a low luminance / a low-amplitude current. Moreover, the disclosed LED quick activation system is substantially free of voltage detection. Therefore, the disclosed LED quick activation system has lower standby power consumption and a simpler circuitry.

[0010] FIG. 1 illustrates a schematic diagram of a LED quick activation system 100 according to one embodiment. In some examples, the LED quick activation system 100 is equipped on a LED device for rapidly driving the LED device to its qualified operational voltage from a standby or cold-start status, i.e., in an extremely short of period.

[0011] The LED quick activation system 100 includes a driving circuit 10, a current control switch 20, a quick discharging module 30, a controller 40, a loading module 50, a power source 60 and a filter capacitor CF.

[0012] The driving circuit 10 is electrically coupled to the power source 60 for receiving power. Also, the driving circuit is electrically coupled to the loading module 50 and the filter capacitor CF in parallel for driving the loading module 50 using a driving current and for charging the filter capacitor CF. In some examples, the power source 60 provides a direct-current (DC) voltage or an alternative-current (AC) voltage. In addition, in some examples, the driving circuit 10 includes at least one or a combination of a transformer, a rectifier, a filter, and other circuits or devices having similar functions.

[0013] The current control switch 20 is electrically coupled to the driving circuit 10 for receiving its driving current. Second, the current control switch 20 is electrically coupled to the controller 40 for receiving a current control signal CI that renders the current control switch 20 to switch on or switch off. Third, the current control switch 20 is electrically coupled to the loading module 50 and the filter capacitor CF in parallel for controlling their input power. Specifically, the current control switch 20 uses pulse-width modulation (PWM) for modulating an input period (or an input frequency) and in turn determines the output power for the loading module 50 and the filter capacitor CF.

[0014] The quick discharging module 30 is electrically coupled to the loading module 50 and the filter capacitor CF in parallel. Also, the quick discharging module 30 rapidly switches the loading module 50 to ground. And the quick discharging module 30 linearly discharges the filter capacitor with the aid of a constant-current false-loading design, such that the filter capacitor CF's discharging period is significantly reduced. The quick discharging module 30's technical details will be introduced later.

[0015] The controller 40 is electrically coupled to the driving circuit 10, the current control switch 20 and the quick discharging module 30 for controlling these elements' respective operations. In some examples, the controller 40 is implemented using at least one or a combination of a CPU (Central Processing Unit), a programmable unit microprocessor that is for general use or specific use, a DSP (Digital Signal Processor), and an ASIC (Application Specific Integrated Circuit). In some examples, the controller 40 may be equipped with a storage unit or be combined with the storage unit to form a SoC (System-on-Chip), such that the controller 40 is capable of permanently or quasi-permanently storing information, which may include a lookup table or multiple sets of operating parameters. And in turn the controller 40 can pre-store required operating parameters for future access or use.

[0016] Primarily, the controller 40 records discharging parameters generated during a discharging period that the quick discharging module 30 discharges the filter capacitor CF last time. In this way, the controller 40 determines an equivalent charging time period for the loading module 50's operational voltage parameters. In addition, based on the determined equivalent charging time period, the controller 40 transmits the current control signal CI to the current control switch 20 for switching the input power to the loading module 50 and the filter capacitor CF. During the equivalent charging time period (i.e., under a first mode), the controller 40 transmits the current control signal CI to the current control switch 20 for outputting a high-power charging current to charge the filter capacitor CF. After the equivalent charging time period passes (i.e., under a second mode), the controller 40 immediately transmits another current control signal CI to the current control switch 20 for switching its output current to a regular charging current that then charges the loading module 50 and the filter capacitor CF.

[0017] FIG. 2 illustrates a detailed diagram of how the quick discharging module 30 interacts with the driving circuit 10, the filter capacitor CF and the loading module 50 according to one example. The quick discharging module 30 includes a first controller 31, a second controller 32, a logic gate 33, a counter 34 and a discharging unit 35.

[0018] The first controller 31 is electrically coupled to the driving circuit 10 for receiving its output driving voltage VD. The second controller 32 is electrically coupled to the filter capacitor CF's output terminal for detecting the filter capacitor CF's cross voltage. The logic gate 33 is respectively and electrically coupled to the first controller 31 and the second controller 32 for receiving respective output control signals. The counter 34 is electrically coupled in between the first controller 31 and the logic gate 33. The discharging unit 35 is electrically coupled to the loading module 50 in parallel.

[0019] In some examples, the first controller 31 and the second controller 32 are implemented as respectively independent SoC chips or both integrated with the controller 40 as a SoC chip. Besides, in some examples, the logic gate 33 is implemented using an AND gate, an OR gate, a NAND gate, or a NOR gate. In some other examples, the logic gate 33's circuitry is altered to various embodiments, for example, by increasing a number of used logic gates and / or inverters, or by modifying its counter's triggering condition.

[0020] After the driving circuit 10 is activated, the first controller 31 compares the driving circuit 10's output voltage VD with a built-in predetermined voltage Vth, which indicates a lower-bound voltage that can charge the filter capacitor CF to the extent that the loading module 50 can normally operate in a significantly short period. When the output voltage VD is higher than the predetermined voltage Vth in voltage level, the first controller 31 outputs a high-level voltage, which is generated by applying a built-in Schmitt trigger's voltage swing, to the counter 34. Upon receiving the high-level voltage, the counter 34 keeps on resetting its count and outputs a first logic parameter PL1 to the logic gate 33's first input terminal. At this time, the second controller 32 senses the filter capacitor CF's high cross voltage, which is charged by via the output voltage VD, and in response outputs a second logic parameter PL2 to the logic gate 33's second input terminal. And the logic gate 33 performs logic calculation on both the received first logic parameter PL1 and the received second logic parameter PL2 to generate a control signal CDC to keep the discharging unit 35 open-circuit. At this time, the driving circuit 10's output voltage VD keeps on charging the filter capacitor CF and the loading module 50.

[0021] Upon the moment when the driving circuit 10 is switched off such that its output voltage VD's voltage level significantly drops below the predetermined voltage Vth, the first controller 31 compares the driving circuit 10's output voltage VD with the predetermined voltage Vth. At this time, the output voltage VD's voltage level is lower than the predetermined voltage Vth's voltage level, such that the first controller 31 outputs a low-level voltage, which is generated by the built-in Schmitt trigger's voltage swing, to the counter 34. At this time, the counter 34's return pin's voltage level is changed from high to low, so the counter 34 starts accumulating its count as a clock. When the counter 34's count exceeds a predetermined upper count, the counter 34 outputs a third logic parameter PL3 to the logic gate 33's first input terminal. At the same time, since the filter capacitor CF hasn't begun discharging itself during the counter 34's counting, the second controller 32 still senses the filter capacitor CF's high cross voltage and keeps on outputting the second logic parameter PL2. Therefore, the logic gate 33 currently receives the third logic parameter PL3 from the counter 34 (i.e., the first controller 31) and the second logic parameter PL2 from the second controller 32. And in turn, the logic gate 33 outputs the control signal CDC to activate (i.e., close-circuit) the discharging unit 35, such that the discharging unit 35 rapidly discharges the filter capacitor CF to a low level (e.g., the ground level).

[0022] At the end of discharging the filter capacitor CF, the counter 34's final count is stored as a discharging parameter by the controller 40. Additionally, the controller 40 is capable of estimating the filter capacitor CF's required charging time period based on the stored discharging parameter without referring to a feedback voltage. The present disclosure discloses two examples of ow the discharging parameter is determined in FIG. 3 and FIG. 4 in a form of equivalent circuit diagram.

[0023] As shown in FIG. 3, the current control switch 20 includes a constant current source A1 and an equivalent transistor. After an initial discharging, the controller 40 confirms a discharging parameter S_th / F_sw, where S_th indicates the counter 34's final count, and F_sw indicates a power transformation switch frequency. With the aid of circuitry setting, the following parameters are known: V_C indicates a LED's barrier voltage (from the loading module 50), X indicates a charging end ratio, I_in indicates a charging current or the driving current from the driving circuit 10, I_L indicates the constant current source A1's constant current, and C indicates the filter capacitor CF's capacitance.

[0024] At initial, a designated target charging voltage V_target, using which the filter capacitor CF's cross voltage reaches at least (i.e., lower-bound) for successfully driving the loading module 50, has to be determined. The controller 40 calculates a target charging voltage V_target as: V_target = V_C × X

[0025] Second, the controller 40 calculates the discharging parameter S_th / F_sw and define said discharging parameter S_th / F_sw as a required discharging period T_Ron, during which the filter capacitor CF discharges to the LED's barrier voltage V_C. The controller 40 calculates the discharging period T_Ron as: T_Ron = S_th / F_sw = M

[0026] It is noted that the discharging period T_Ron can be replaced by other characteristic parameters in other examples.

[0027] Third, the controller 40 calculates a charging voltage V_(C, TRon) that the filter capacitor CF's cross voltage can reach during the same period as the discharging period T_Ron as: V_ C , TRon = M × I_in / C

[0028] Fourth, the controller 40 calculates a charging time period T_Roff, during which the charging voltage V_(C, TRon) takes to charge till reaching the target charging voltage V_target, as: T_Roff = V_target − V_ C , TRon × I_in / C

[0029] Last, the controller 40 calculates an equivalent charging time period T, during which the filter capacitor CF requires to charge, as a sum of the discharging period T_Ron and the charging time period T_Roff, i.e., as: T = T_Ron + T_Roff = M + V_C × X − M × I_in / C × I_in / C

[0030] In another example, as shown in FIG. 4, the current control switch 20 includes a constant resistor R1 and an equivalent transistor. After an initial discharging, the controller 40 confirms the discharging parameter S_th / F_sw , where S_th and F_sw shares same definitions as abovementioned. Similarly, with the aid of circuitry setting, the following parameters are also known: V_C indicates the LED's barrier voltage (from the loading module 50), X indicates the charging end ratio, I_in indicates the charging current, I_L indicates the constant current source A1's constant current, C indicates the filter capacitor CF's capacitance, and R indicates the constant resistor R1's resistance.

[0031] At initial, the designated target charging voltage V_target, which the filter capacitor CF's cross voltage at least (i.e., lower-bound) reaches for successfully driving the loading module 50, has to be determined. The controller 40 calculates the target charging voltage V_target as: V_target = V_C × X

[0032] Second, the controller 40 calculates the discharging parameter S_th / F_sw and define said discharging parameter S_th / F_sw as the required discharging period T_Ron, during which the filter capacitor CF discharges to the LED's barrier voltage V_C. The controller 40 calculates the discharging period T_Ron as: T_Ron = S_th / F_sw = M

[0033] It is noted that the discharging period T_Ron can be replaced by other characteristic parameters in other examples.

[0034] Third, the controller 40 calculates a charging voltage V_(C, TRon) that the filter capacitor CF's cross voltage can reach during the same period as the discharging period T_Ron as: V_ C , TRon = I_in × M / C / 1 + M / RC

[0035] Fourth, the controller 40 calculates the charging time period T_Roff, during which the charging voltage V_(C, TRon) takes to charge till reaching the target charging voltage V_target, as: T_Roff = V_target − V_ C , TRon × I_in / C

[0036] Last, the controller 40 calculates an equivalent charging time period T, during which the filter capacitor CF requires to charge, as a sum of the discharging period T_Ron and the charging time period T_Roff, i.e., as: T = T_Ron + T_Roff = M + V_C × X − I_in × M / C / 1 + M / RC × I_in / C

[0037] With the aid of the first example (i.e., formulas (1)-(5)) and the second example (i.e., formulas (6)-(10)), the controller 40 is capable of calculating the filter capacitor CF's required charging time period T. Based on the charging time period T, the controller 40 can operate under two different charging modes. Under a first mode that corresponds to the equivalent charging time period T, the driving circuit 10 that is under the controller 40's control charges the filter capacitor CF with a high-power charging current. And under a second mode that after the equivalent charging time period T passes, the driving circuit 10 that is under the controller 40's control switches to a regular charging current for charging the loading module 50 and the filter capacitor CF, such that the controller 40 is able to immediately activate the loading module 50, specifically, its LED units.

[0038] FIG. 5 illustrates a flowchart of a quick activation method that the LED quick activation system 100 applies according to one embodiment. In some examples, the disclosed quick activation method in a form of software or firmware is installed in a processor for execution. The disclosed quick activation method may also be implemented using multiple chips and their circuitry.

[0039] In Step S01, during a preceding switch-off of the LED quick activation system 100, the controller records a discharging parameter, which may be the filter capacitor CF's discharging period, the counter 34's count, or other parameters that are positively associated with the filter capacitor CF's discharging period.

[0040] In Step S02, the controller 40 determines the equivalent charging time period T according to the filter capacitor CF's discharging parameter. During the equivalent charging time period T, the controller 40's calculation may vary corresponding to different types of circuitry.

[0041] In Step S03, the controller 40 transmits the control signal CI to the current control switch 20 for switching the driving circuit 10's input power to the loading module 50 and the filter capacitor CF. Specifically, the controller 40 switches between the abovementioned first and second modes. During the first mode, i.e., during the equivalent charging time period T, the controller 40 relays the current control signal CI of a first level to the current control switch 20 for outputting a high-power charging current (i.e., of a charging amplitude) to charge the filter capacitor CF. During the second mode, i.e., after the equivalent charging time period T passes, the controller 40 relays the current control signal CI of a second level to the current control switch 20 for switching to output a regular-power current (i.e., of a regular amplitude) for charging the loading module 50 and the filter capacitor CF. Based on the switching between the first mode and the second mode, the LED quick activation system 100 is capable of charging the filter capacitor CF's cross voltage to the extent that the loading module 50 can normally operate (i.e., the loading module 50's LED units to normally illuminate) in a significantly short period, such that the LED quick activation system 100 can perform its quick-start function.

[0042] In conclusion, the disclosed LED activation system 100 can rapidly charge its filter capacitor CF upon the driving circuit 10 switches from an OFF state to an ON state. In this way, even though the disclosed LED activation system 100 receives a low-amplitude current, it still activates the loading module 50's LED units in a significantly short period. On top of that, the disclosed LED activation system 100 is substantially free from detecting a feedback voltage for required control. Therefore, the disclosed LED activation system 100 has the following advantages: (1) the controller 40's less pins; (2) no voltage-dividing resistor is required; (3) no regular power consumption caused by detecting the feedback voltage occurs; (4) lower standby power consumption (because of substantially free from feedback voltage detection); and (5) the disclosed LED activation system 100's simpler circuitry.

Claims

1. An LED quick activation system (100), comprising: a driving circuit (10) which is configured to generate an output driving voltage (VD) and a driving current using a received power; a loading module (50) which is electrically coupled to the driving circuit (10), and configured to illuminate its LED unit using the output driving voltage and the driving current; a filter capacitor (CF) which is electrically coupled to the loading module (50) in parallel, and is configured to charge its cross voltage using the output driving voltage or discharge its cross voltage to ground; a current control switch (20) which is electrically coupled to the driving circuit (10) configured for receiving the driving current, and is configured to control input power to the loading module (50) and the filter capacitor (CF); a quick discharging module (30) which is electrically coupled to the loading module (50) and the filter capacitor (CF) in parallel, and is configured to discharge the filter capacitor (CF) to the ground; and characterized in that, the LED quick activation system (100) further comprises a primary controller (40) electrically coupled to the driving circuit (10), the current control switch (20) and the quick discharging module (30), wherein the primary controller (40) is configured to: store a discharging parameter calculated during a period that the quick discharging module (30) discharges the filter capacitor (CF), calculate an equivalent charging time period (T) for charging the filter capacitor (CF)'s cross voltage to a target charging voltage using the discharging parameter, control the current control switch (20) to charge the filter capacitor (CF) and the loading module (50) using the driving current of a charging amplitude during the equivalent charging period, and charge the filter capacitor (CF) and the loading module (50) using the driving current of a regular amplitude after the equivalent charging period passes; wherein the equivalent charging period is a sum of a discharging period (T_Ron) and a charging period (T_Roff) of the filter capacitor (CF), and wherein the target charging voltage refers to a lower-bound voltage that charges the filter capacitor (CF) to the extent that the loading module (50) normally operates in a significantly short period; wherein the quick discharging module (30) comprises: a first controller (31) which is electrically coupled to the driving circuit (10) for receiving the output driving voltage; a second controller (32) which is electrically coupled to the filter capacitor (CF)'s output terminal configured for detecting the filter capacitor (CF)'s cross voltage; a logic gate (33), which is respectively and electrically coupled to the first controller and the second controller, configured for receiving respective output control signals; a counter (34), electrically coupled in between the first controller (31) and the logic gate; and a discharging unit (35) which is electrically coupled to the loading module (50) in parallel; wherein the first controller (31) is further configured to compare the output driving voltage with the target charging voltage; wherein when the output driving voltage (VD) of the driving circuit (10) is higher than the target charging voltage, the first controller (31) is further configured to output a high-level voltage to the counter (34), and the counter (34) is further configured to in turn keep on resetting the counter (34)'s count and output a first logic parameter (PL1) that corresponds to the high-level voltage to the logic gate's first input terminal; wherein the second controller (32) is further configured to sense the filter capacitor (CF)'s cross voltage that exceeds the target charging voltage, and correspondingly generate a second logic parameter (PL2) that corresponds to the filter capacitor (CF)'s cross voltage to the logic gate's second input terminal; and wherein the logic gate is further configured to perform a logic calculation on both the first logic parameter and the second logic parameter to keep the discharging unit (35) open-circuit, such that the output driving voltage keeps on charging the filter capacitor (CF) and the loading module (50); wherein the first controller (31) is further configured to compare the output driving voltage with the target charging voltage; wherein when the output driving voltage (VD) of the driving circuit (10) is lower than the target charging voltage, the first controller (31) is further configured to output a low-level voltage to the counter (34); wherein the counter (34) is further configured to in turn accumulate its count as a clock, and is further configured to output a third logic parameter (PL3) to the logic gate's first input terminal; wherein during the counter's count accumulation the filter capacitor (CF) begins discharging its cross voltage, such that the second controller (32) still senses the filter capacitor (CF)'s cross voltage and correspondingly generates the second logic parameter (PL2); wherein the logic gate is further configured to perform a logic calculation on both the third logic parameter and the second logic parameter, and to in turn activate the discharging unit (35); and wherein when the discharging unit (35) is activated; the discharging unit (35) discharges the filter capacitor (CF) to a ground level, and the primary controller (40) is further configured to store the counter (34)'s final count as the discharging parameter; wherein the current control switch (20) comprises a constant resistor (R1) and a corresponding transistor; wherein the primary controller (40) is further configured to calculate the target charging voltage as: V_target = V_C × X ; wherein V_target represents the target charging voltage, V_C represents the loading module (50)'s LED barrier voltage, and X represents a charging end ratio; wherein the primary controller (40) is further configured to calculate the discharging period of the filter capacitor (CF) as: T_Ron = S_th / F_sw = M ; wherein T_Ron and M represent the discharging period, S_th represents the counter (34)'s final count, and F_sw represents a power transformation switch frequency; wherein the primary controller (40) is further configured to calculate a charging voltage that the filter capacitor (CF)'s cross voltage reaches during the same period as the discharging period as: V_ C , TRon = I_in × M / C / 1 + M / RC ; wherein V_(C, TRon) represents the charging voltage, M represents the discharging period, I_in represents the driving current from the driving circuit (10), C represents the filter capacitor (CF)'s capacitance, and R represents the constant resistor's resistance; wherein the primary controller (40) is further configured to calculate a charging period, during which the charging voltage takes to charge till reaching the target charging voltage, as: T_Roff = V_target − V_ C , TRon × I_in / C ; wherein T_Roff i represents the charging period, V_(C, TRon) represents the charging voltage, V_target represents the target charging voltage, I_in represents the driving current from the driving circuit (10), and C represents the filter capacitor (CF)'s capacitance.

2. The LED quick activation system (100) of claim 1, characterized in that, the primary controller (40) is further configured to calculate the equivalent charging period as: T = T_Ron + T_Roff = M + V_C × X − I_in × M / C / 1 + M / RC × I_in / C ; wherein T represents the equivalent charging period, T_Ron and M represent the discharging period, T_Roff represents the charging period, V_C represents the loading module (50)'s LED barrier voltage, X represents a charging end ratio, I_in represents the driving current from the driving circuit (10), C represents the filter capacitor (CF)'s capacitance, and R represents the constant resistor's resistance.

3. The LED quick activation system (100) of claim 1, characterized in that, the primary controller (40) is implemented using at least one or a combination of a CPU, a programmable unit microprocessor for general use or specific use, a digital signal processor, and an application specific integrated circuit.