Cyclic Division Method and Procedure for Phase Noise Compensation in CP-OFDM

Abstract

This specification discloses multiple embodiments for dealing with wireless communication, and one or more of the embodiments, in particular, address phase noise (PN) compensation techniques where multiple groups of reference symbols are transmitted by a calculated division into groups of an appropriate size of the allocated physical resource blocks (PRBs) (e.g., below the coherence bandwidth of the channel), and frequency-domain circularly symmetric transmission from the transmitting entity that adds cyclic subcarriers to each group is ensured. There may be one or more designs of techniques for selecting groups of appropriate number and size to enable appropriate levels of PN compensation at the receiving entity and for providing various ways to ensure circular symmetry within each group. One or more approaches may be capable of adapting to the instantaneous channel state and PN characteristics of the transceiver for each user.

Description

Technical Field

[0001] (Cross - Reference to Related Applications) This application claims the benefit of U.S. Provisional Patent Application No. 63 / 346,180, filed May 26, 2022, and U.S. Provisional Patent Application No. 63 / 394,452, filed Aug. 2, 2022, the contents of which are incorporated herein by reference.

Background Art

[0002] In a wireless system, a wireless device (receiving or transmitting) must address problems that can occur in signals. As wireless technology advances, it is necessary to ensure that these problems can be addressed with one or more new approaches.

Summary of the Invention

[0003] This specification discloses multiple embodiments for dealing with wireless communication. One or more of the embodiments, in particular, address phase noise (PN) compensation techniques where multiple groups of reference symbols are transmitted by a calculated partitioning into groups of an appropriate size of the allocated Physical Resource Block (PRB) (e.g., below the coherence bandwidth of the channel), and frequency - domain circular - symmetric transmission from the transmitting entity adding cyclic sub - carriers to each group is ensured. There may be one or more designs for selecting appropriate numbers and sizes of groups to enable appropriate levels of PN compensation at the receiving entity and for providing various methods to ensure circular symmetry within each group. One or more approaches may be capable of adapting to the instantaneous channel state and PN characteristics of the transceiver for each user (e.g., device).

Brief Description of the Drawings

[0004] A more detailed understanding can be obtained from the following description given by way of example in conjunction with the accompanying drawings, where like reference numerals in the figures indicate like elements.

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[0005] In this specification, multiple embodiments, examples, techniques, and approaches for dealing with wireless communication are disclosed. One or more of the approaches, in particular, address phase noise (PN) compensation techniques where multiple groups of reference symbols are transmitted by a calculated division into groups of an appropriate size of the allocated physical resource blocks (PRBs) (e.g., below the coherence bandwidth of the channel), and frequency domain circular symmetric transmission from the transmitting entity that adds cyclic subcarriers to each group is guaranteed. Appropriate numbers and sizes of groups can be selected to enable appropriate levels of PN compensation in the receiving entity, and there may be one or more techniques for ensuring circular symmetry within each group. One or more approaches may be capable of adapting to the instantaneous channel state and PN characteristics of the transceiver for each user (e.g., for each device).

[0006] Furthermore, this specification discloses a plurality of methods for wireless communication, one or more of which are, in particular, for phase noise compensation in transmission based on cyclic partitioning of subcarriers, having the ability to adapt to the instantaneous channel state and / or the phase noise characteristics of the transceiver for each user (e.g., for each device). One or more of these methods may include obtaining phase noise information characterizing the amount of phase noise experienced in a communication link. One or more of the methods may include determining the coherence bandwidth B coh of the channel. One or more of the methods may include selecting default values of the subcarrier group size M, the length L coh of the frequency-domain cyclic prefix, and the length L CP of the frequency-domain cyclic suffix based on B CS and the phase noise information. One or more of the methods may include determining whether a high phase noise indication is reported by the receiving entity and / or whether the coherence bandwidth of the channel is lower than the user's allocated bandwidth in order to adapt the subcarrier cyclic partitioning parameters M, L CP and L CS to the instantaneous conditions. One or more of the methods may include updating the values of L CP and L CS based on a high phase noise indication received from the receiving entity. One or more of the methods may include performing a rate matching function to adjust the amount of data mapped to the available physical resources after considering the frequency-domain cyclic prefix field and / or the frequency-domain cyclic suffix field. One or more of the methods may include sending signaling information including, for example, the values of M, L CP and L CS . One or more of the methods may include transmitting CP-OFDM symbols.

[0007] Furthermore, this specification discloses a plurality of methods for wireless communication, one or more of which are, in particular, for phase noise compensation in reception based on cyclic division of subcarriers, having the ability to adapt to the instantaneous channel state for each user and / or the phase noise characteristics of the transceiver. One or more of the methods may include receiving CP-OFDM symbols. One or more of the methods may include performing channel estimation, equalization, and / or common phase error compensation in the frequency domain of the received CP-OFDM. One or more of the methods may include obtaining, for example, via signaling indication, the subcarrier group size M, and the length L of the frequency domain cyclic prefix CP and / or the length L of the frequency domain cyclic suffix CS . One or more of the methods may include, based on M, L greater than 0 CP and / or L CS , averaging the estimated phase noise inter-carrier interference (ICI) components in each subcarrier group and performing phase noise ICI compensation. One or more of the methods may include demodulating the subcarriers and comparing the residual phase noise ICI power with a threshold. One or more of the methods may include determining phase noise characteristics, such as the phase noise spectral width, based on the residual phase noise ICI power exceeding the threshold. One or more of the methods may include sending a high phase noise indication including information regarding the amount of phase noise expected or experienced in the communication link, such as phase noise capability information and / or phase noise spectral width.

[0008] FIG. 1A is a diagram illustrating an exemplary communication system 100 in which one or more of the disclosed embodiments may be implemented. The communication system 100 may be a multiple access system that provides content such as voice, data, video, messaging, broadcast, etc. to a plurality of wireless users. The communication system 100 may enable a plurality of wireless users to access such content through sharing of system resources including wireless bandwidth. For example, the communication system 100 may use one or more channel access methods such as code division multiple access (CDMA), time division multiple access (TDMA), frequency division multiple access (FDMA), orthogonal FDMA (OFDMA), single-carrier FDMA (SC-FDMA), zero-tail unique-word discrete Fourier transform Spread OFDM (ZT-UW-DFT-S-OFDM), unique word OFDM (UW-OFDM), resource block filter type OFDM, filter bank multicarrier (FBMC).

[0009] As shown in FIG. 1A, communication system 100 may include wireless transmit / receive units (WTRUs) 102a, 102b, 102c, 102d, a radio access network (RAN) 104, a core network (CN) 106, a public switched telephone network (PSTN) 108, the Internet 110, and other networks 112, but it will be understood that the disclosed embodiments contemplate any number of WTRUs, base stations, networks, and / or network elements. Each of the WTRUs 102a, 102b, 102c, 102d can be any type of device configured to operate and / or communicate in a wireless environment. By way of example, the WTRUs 102a, 102b, 102c, 102d, all of which may be referred to as stations (STAs), can be configured to transmit and / or receive wireless signals and can include user equipment (UE), mobile stations, fixed or mobile telephone subscriber units, subscriber-based units, pagers, cellular telephones, personal digital assistants (PDAs), smartphones, laptops, netbooks, personal computers, wireless sensors, hotspots or Mi-Fi devices, Internet of Things (IoT) devices, watches or other wearables, head-mounted displays (HMDs), vehicles, drones, medical devices and applications (e.g., remote surgery), industrial devices and applications (e.g., robots and / or other wireless devices operating in an industrial and / or automated processing chain context), home appliances, devices operating in commercial and / or industrial wireless networks, etc. Any of the WTRUs 102a, 102b, 102c, and 102d can be interchangeably referred to as a UE. Any reference to a "user" made herein can be interchangeable with the user's device and / or WTRU. For example, when bandwidth is allocated to a user, this is equivalent to when bandwidth is allocated to a WTRU by receiving a configuration grant for a particular bandwidth to be used.

[0010] The communication system 100 may also include base station 114a and / or base station 114b. Each of base stations 114a, 114b may be any type of device configured to wirelessly interface with at least one of WTRUs 102a, 102b, 102c, 102d to facilitate access to one or more communication networks such as CN 106, Internet 110, and / or other network 112. By way of example, base stations 114a, 114b may be a base transceiver station (BTS), Node B, eNode B (eNB), home Node B, home eNode B, next generation Node B (gNode B (gNB), etc.), new radio (NR) Node B, site controller, access point (AP), wireless router, and the like. Base stations 114a, 114b are each depicted as a single element, but it will be understood that base stations 114a, 114b may include any number of interconnected base stations and / or network elements.

[0011] Base station 114a can be part of RAN104, which can also include other base stations such as a base station controller (BSC), a radio network controller (RNC), a relay node, and / or network elements (not shown). Base station 114a and / or base station 114b can be configured to transmit and / or receive radio signals at one or more carrier frequencies that can be referred to as a cell (not shown). These frequencies can be licensed spectrum, unlicensed spectrum, or a combination of licensed and unlicensed spectrum. A cell can provide wireless service coverage to a specific geographic area that can be relatively fixed or can change over time. A cell can be further divided into cell sectors. For example, the cell associated with base station 114a can be divided into three sectors. Thus, in one embodiment, base station 114a can include three transceivers, i.e., one transceiver per sector of the cell. In one embodiment, base station 114a can employ multiple-input multiple output (MIMO) technology and can utilize multiple transceivers per sector of the cell. For example, beamforming can be used to transmit and / or receive signals in a desired spatial direction.

[0012] Base stations 114a, 114b can communicate with one or more of WTRUs 102a, 102b, 102c, 102d via air interface 116, which can be any suitable wireless communication link (e.g., radio frequency (RF), microwave, centimeter wave, micrometer wave, infrared (IR), ultraviolet (UV), visible light, etc.). Air interface 116 can be established using any suitable radio access technology (RAT).

[0013] More specifically, as described above, the communication system 100 can be a multiple access system and can adopt one or more channel access methods such as CDMA, TDMA, FDMA, OFDMA, SC-FDMA, etc. For example, the base stations 114a of RAN104 and the WTRUs 102a, 102b, 102c can implement radio technologies such as Universal Mobile Telecommunications System (UMTS) Terrestrial Radio Access (UTRA) that can establish the air interface 116 using wideband CDMA (WCDMA). WCDMA can include communication protocols such as High-Speed Packet Access (HSPA) and / or Evolved HSPA (HSPA+). HSPA can include High-Speed Downlink Packet Access (HSDPA) and / or High-Speed Uplink Packet Access (HSUPA).

[0014] In one embodiment, the base stations 114a and the WTRUs 102a, 102b, 102c can implement radio technologies such as Evolved UMTS Terrestrial Radio Access (E-UTRA), which can establish the air interface 116 using Long Term Evolution (LTE) and / or LTE-Advanced (LTE-A) and / or LTE-Advanced Pro (LTE-A Pro).

[0015] In one embodiment, the base stations 114a and the WTRUs 102a, 102b, 102c can implement radio technologies such as NR radio access, which can establish the air interface 116 using NR.

[0016] In one embodiment, base station 114a and WTRUs 102a, 102b, 102c may implement multiple radio access technologies. For example, base station 114a and WTRUs 102a, 102b, 102c may implement LTE radio access and NR radio access together, for example, using the dual connectivity (DC) principle. Accordingly, the air interface utilized by WTRUs 102a, 102b, 102c may be characterized by transmissions sent between multiple types of radio access technologies and / or multiple types of base stations (e.g., eNBs and gNBs).

[0017] In other embodiments, base station 114a and WTRUs 102a, 102b, 102c may implement wireless technologies such as IEEE 802.11 (i.e., Wireless Fidelity (WiFi)), IEEE 802.16 (i.e., Worldwide Interoperability for Microwave Access (WiMAX)), CDMA2000, CDMA2000 1X, CDMA2000 EV-DO, Interim Standard 2000 (IS-2000), IS-95, IS-856, Global System for Mobile communications (GSM), Enhanced Data rates for GSM Evolution (EDGE), GSM EDGE (GERAN), etc.

[0018] The base station 114b in Fig. 1A can be, for example, a wireless router, a home node B, a home e-node B, or an access point, and can utilize any suitable RAT to facilitate wireless connections in a local area such as an office, a home, a vehicle, a campus, an industrial facility, an aerial corridor (e.g., for use by a drone), a road, etc. In one embodiment, the base station 114b and the WTRUs 102c, 102d can implement a wireless technology such as IEEE 802.11 to establish a wireless local area network (WLAN). In one embodiment, the base station 114b and the WTRUs 102c, 102d can implement a wireless technology such as IEEE 802.15 to establish a wireless personal area network (WPAN). In yet another embodiment, the base station 114b and the WTRUs 102c, 102d can utilize a cellular-based RAT (e.g., WCDMA, CDMA2000, GSM, LTE, LTE-A, LTE-A Pro, NR, etc.) to establish a pico cell or a femto cell. As shown in Fig. 1A, the base station 114b can have a direct connection to the Internet 110. Thus, the base station 114b may not need to access the Internet 110 via the CN 106.

[0019] RAN 104 can communicate with CN 106, which can be any type of network configured to provide voice, data, applications, and / or voice over internet protocol (VoIP) services to one or more of WTRUs 102a, 102b, 102c, 102d. The data can have various quality of service (QoS) requirements, such as different throughput requirements, latency requirements, error tolerance requirements, reliability requirements, data throughput requirements, mobility requirements, etc. CN 106 can provide call control, billing services, mobile location-based services, prepaid calls, internet connections, video distribution, etc., and / or perform high-level security functions such as user authentication. Although not shown in FIG. 1A, it will be understood that RAN 104 and / or CN 106 can communicate directly or indirectly with other RANs using the same or different radio access technologies (RATs) as RAN 104. For example, in addition to being connected to a RAN 104 that can utilize New Radio (NR) radio technology, CN 106 can also communicate with another RAN (not shown) using GSM, UMTS, CDMA2000, WiMAX, E-UTRA, or WiFi radio technology.

[0020] CN106 may also function as a gateway for the WTRU102a, 102b, 102c, 102d to access the PSTN108, the Internet 110, and / or other networks 112. The PSTN108 may include a circuit-switched telephone network that provides a plain old telephone service (POTS). The Internet 110 may include a global system of interconnected computer networks and devices, where these networks and devices use a common communication protocol such as the transmission control protocol (TCP), the user datagram protocol (UDP), and / or the internet protocol (IP) of the TCP / IP internet protocol suite. The network 112 may include a wired communication network and / or a wireless communication network that is owned and / or operated by another service provider. For example, the network 112 may include another CN connected to one or more RANs, which may use the same RAT as the RAN 104 or a different RAT.

[0021] Some or all of the WTRU102a, 102b, 102c, 102d in the communication system 100 may include a multi-mode function (e.g., the WTRU102a, 102b, 102c, 102d may include multiple transceivers for communicating with different wireless networks via different wireless links). For example, the WTRU102c shown in Figure 1A may be configured to communicate with a base station 114a that may employ a cellular-based wireless technology and a base station 114b that may employ IEEE802 wireless technology.

[0022] Figure 1B is a system diagram illustrating an exemplary WTRU 102. As shown in Figure 1B, the WTRU 102 may include, among other things, a processor 118, a transceiver 120, a transmit / receive element 122, a speaker / microphone 124, a keypad 126, a display / touchpad 128, a non-removable memory 130, a removable memory 132, a power supply 134, a global positioning system (GPS) chipset 136, and / or other peripheral devices 138. It will be understood that the WTRU 102 may include any partial combination of the foregoing elements while remaining consistent with one embodiment.

[0023] The processor 118 can be a general-purpose processor, a dedicated processor, a conventional processor, a digital signal processor (DSP), a plurality of microprocessors, one or more microprocessors associated with a DSP core, a controller, a microcontroller, an application specific integrated circuit (ASIC), a field programmable gate array (FPGA), any other type of integrated circuit (IC), a state machine, etc. The processor 118 can perform signal coding, data processing, power control, input / output processing, and / or any other function that enables the WTRU 102 to operate in a wireless environment. The processor 118 can be coupled to a transceiver 120 that can be coupled to a transmit / receive element 122. Although Figure 1B depicts the processor 118 and the transceiver 120 as separate components, it will be understood that the processor 118 and the transceiver 120 can be integrated together in an electronic package or chip.

[0024] The transmit / receive element 122 may be configured to transmit signals to or receive signals from a base station (e.g., base station 114a) via the air interface 116. For example, in one embodiment, the transmit / receive element 122 may be an antenna configured to transmit and / or receive RF signals. In one embodiment, the transmit / receive element 122 may be an emitter / detector configured to transmit and / or receive, for example, IR signals, UV signals, or visible light signals. In yet another embodiment, the transmit / receive element 122 may be configured to transmit and / or receive both RF signals and optical signals. It will be understood that the transmit / receive element 122 may be configured to transmit and / or receive any combination of wireless signals.

[0025] Although the transmit / receive element 122 is depicted in FIG. 1B as a single element, the WTRU 102 may include any number of transmit / receive elements 122. More specifically, the WTRU 102 may employ MIMO technology. Thus, in one embodiment, the WTRU 102 may include two or more transmit / receive elements 122 (e.g., multiple antennas) for transmitting and receiving wireless signals via the air interface 116.

[0026] The transceiver 120 may be configured to modulate signals transmitted by the transmit / receive element 122 and demodulate signals received by the transmit / receive element 122. As noted above, the WTRU 102 may have a multimode function. Thus, the transceiver 120 may include multiple transceivers to enable the WTRU 102 to communicate via multiple RATs such as, for example, NR and IEEE 802.11.

[0027] The processor 118 of the WTRU 102 may be coupled to the speaker / microphone 124, keypad 126, and / or the display / touchpad 128 (e.g., a liquid crystal display (LCD) display unit or an organic light-emitting diode (OLED) display unit), and may receive data input by a user therefrom. The processor 118 may also output user data to the speaker / microphone 124, keypad 126, and / or the display / touchpad 128. In addition, the processor 118 may access information from and store data in any type of suitable memory, such as the non-removable memory 130 and / or the removable memory 132. The non-removable memory 130 may include random-access memory (RAM), read-only memory (ROM), a hard disk, or any other type of memory storage device. The removable memory 132 may include a subscriber identity module (SIM) card, a memory stick, a secure digital (SD) memory card, and the like. In other embodiments, the processor 118 may access information from and store data in a memory that is not physically located on the WTRU 102, such as on a server or a home computer (not shown).

[0028] The processor 118 may receive power from the power supply 134 and may be configured to distribute and / or control power to other components in the WTRU 102. The power supply 134 may be any suitable device for supplying power to the WTRU 102. For example, the power supply 134 may include one or more dry batteries (e.g., nickel-cadmium (NiCd), nickel-zinc (NiZn), nickel metal hydride (NiMH), lithium-ion (Li-ion), etc.), solar cells, fuel cells, and the like.

[0029] The processor 118 may also be coupled to the GPS chipset 136, which may be configured to provide location information (e.g., longitude and latitude) regarding the current location of the WTRU 102. In addition to, or instead of, information from the GPS chipset 136, the WTRU 102 may receive location information from a base station (e.g., base stations 114a, 114b) via the air interface 116 and / or may determine its location based on the timing of signals received from two or more neighboring base stations. It will be understood that the WTRU 102 may obtain location information by any suitable location determination method while remaining consistent with one embodiment.

[0030] Processor 118 may be further coupled to other peripheral devices 138, which may include one or more software and / or hardware modules that provide additional features, functionality, and / or wired or wireless connections. For example, peripheral devices 138 may include an accelerometer, an electronic compass, a satellite transceiver, a digital camera (for photos and / or videos), a universal serial bus (USB) port, a vibration device, a television transceiver, a hands-free headset, a Bluetooth® module, a frequency modulated (FM) radio unit, a digital music player, a media player, a video game player module, an Internet browser, a Virtual Reality / Augmented Reality (VR / AR) device, an activity tracker, etc. Peripheral devices 138 may include one or more sensors. The sensors may be one or more of a gyroscope, an accelerometer, a Hall effect sensor, a magnetometer, an orientation sensor, a proximity sensor, a temperature sensor, a time sensor, a geolocation sensor, an altimeter, a light sensor, a touch sensor, a magnetometer, a barometer, a gesture sensor, a biometric sensor, a humidity sensor, etc.

[0031] The WTRU 102 may include a full-duplex radio in which some or all of the transmission and reception of signals (e.g., associated with specific subframes for UL (e.g., for transmission) and DL (e.g., for reception)) may be simultaneous and / or together. The full-duplex radio may include an interference management unit for reducing and / or substantially eliminating self-interference either via hardware (e.g., a choke) or via signal processing through a processor (e.g., a separate processor (not shown) or via processor 118). In one embodiment, the WTRU 102 may include a half-duplex radio for some or all of the transmission and reception of signals (e.g., associated with specific subframes for either UL (e.g., for transmission) or DL (e.g., for reception)).

[0032] Figure 1C is a system diagram illustrating RAN 104 and CN 106 according to one embodiment. As described above, RAN 104 may employ E-UTRA radio technology to communicate with WTRUs 102a, 102b, 102c via air interface 116. RAN 104 may also communicate with CN 106.

[0033] RAN 104 may include eNodeBs 160a, 160b, 160c, but it will be understood that RAN 104 may include any number of eNodeBs while remaining consistent with one embodiment. Each of eNodeBs 160a, 160b, 160c may include one or more transceivers for communicating with WTRUs 102a, 102b, 102c via air interface 116. In one embodiment, eNodeBs 160a, 160b, 160c may implement MIMO technology. Thus, eNodeB 160a, for example, may transmit wireless signals to and / or receive wireless signals from WTRU 102a using multiple antennas.

[0034] Each of eNodeBs 160a, 160b, 160c may be associated with a particular cell (not shown) and may be configured to handle radio resource management decisions, handover decisions, user scheduling in UL and / or DL, etc. As shown in Figure 1C, eNodeBs 160a, 160b, 160c may communicate with each other via the X2 interface.

[0035] CN 106 shown in Figure 1C may include a mobility management entity (MME) 162, a serving gateway (SGW) 164, and a packet data network (PDN) gateway (PGW) 166. Although the foregoing elements are depicted as part of CN 106, it will be understood that any of these elements may be owned and / or operated by entities other than the CN operator.

[0036] The MME 162 can be connected to each of the eNodeBs 162a, 162b, 162c in the RAN 104 via the S1 interface and can function as a control node. For example, the MME 162 can authenticate users of the WTRUs 102a, 102b, 102c, activate / deactivate bearers, select a specific serving gateway during the initial attach of the WTRUs 102a, 102b, 102c, etc. The MME 162 can provide control plane functions for switching between the RAN 104 and other RANs (not shown) that employ other radio technologies such as GSM and / or WCDMA.

[0037] The SGW 164 can be connected to each of the eNodeBs 160a, 160b, 160c in the RAN 104 via the S1 interface. The SGW 164 can generally route and transfer user data packets between the WTRUs 102a, 102b, 102c. The SGW 164 can perform other functions such as anchoring the user plane during handover between eNodeBs, triggering paging when DL data is available to the WTRUs 102a, 102b, 102c, and managing and storing the context of the WTRUs 102a, 102b, 102c.

[0038] The SGW 164 can be connected to the PGW 166, and the PGW 166 can provide the WTRUs 102a, 102b, 102c with access to a packet switched network such as the Internet 110 to facilitate communication between the WTRUs 102a, 102b, 102c and IP-enabled devices.

[0039] CN106 can facilitate communication with other networks. For example, CN106 can provide access to a circuit-switched network such as the PSTN 108 to the WTRUs 102a, 102b, 102c to facilitate communication between the WTRUs 102a, 102b, 102c and a conventional landline communication device. For example, CN106 can include, or communicate with, an IP gateway (e.g., an IP multimedia subsystem (IMS) server) that functions as an interface between CN106 and the PSTN 108. Additionally, CN106 can provide the WTRUs 102a, 102b, 102c with access to another network 112, which can include other wired and / or wireless networks owned and / or operated by other service providers.

[0040] The WTRU is described as a wireless terminal in FIGS. 1A-1D, but in certain representative embodiments, it is contemplated that such a terminal can use (e.g., temporarily or permanently) a wired communication interface with a communication network.

[0041] In a representative embodiment, the other network 112 can be a WLAN.

[0042] A WLAN in Infrastructure Basic Service Set (BSS) mode may have an access point (AP) of the BSS and one or more stations (STAs) associated with the AP. The AP may have an access or interface to a Distribution System (DS) or another type of wired / wireless network that carries traffic within and / or outside the BSS. Traffic to an STA originating from outside the BSS may reach and be delivered to the STA through the AP. Traffic originating from an STA to a destination outside the BSS may be sent to the AP to be delivered to their respective destinations. Traffic between STAs within the BSS may be sent, for example, through the AP. The source STA may send traffic to the AP, and the AP may deliver the traffic to the destination STA. Traffic between STAs within the BSS may be considered and / or referred to as peer-to-peer traffic. Peer-to-peer traffic may be sent between the source STA and the destination STA (e.g., directly between them) using direct link setup (DLS). In certain representative embodiments, DLS may use 802.11e DLS or 802.11z tunneled DLS (TDLS). A WLAN using Independent BSS (IBSS) mode may not have an AP, and STAs within or using the IBSS (e.g., all of the STAs) may communicate directly with each other. The IBSS mode of communication may be referred to herein as the "ad hoc" communication mode.

[0043] When using the 802.11ac infrastructure operation mode or a similar operation mode, the AP may transmit beacons on a fixed channel such as the primary channel. The primary channel may have a fixed width (e.g., a 20 MHz bandwidth) or a dynamically set width. The primary channel may be the operating channel of the BSS, but it can also be used by the STA to establish a connection with the AP. In certain representative embodiments, Carrier Sense Multiple Access with Collision Avoidance (CSMA / CA) can be implemented, for example, in an 802.11 system. In the case of CSMA / CA, STAs including the AP (e.g., all STAs) can sense the primary channel. If the primary channel is sensed / detected and / or determined to be busy by a particular STA, the particular STA may back off. Only one STA (e.g., only one station) can transmit at any given time in a given BSS.

[0044] A High Throughput (HT) STA may use a 40 MHz wide channel for communication, and this 40 MHz wide channel can be formed, for example, through a combination of the primary 20 MHz channel and an adjacent or non - adjacent 20 MHz channel.

[0045] A Very High Throughput (VHT) STA can support channels with widths of 20 MHz, 40 MHz, 80 MHz, and / or 160 MHz. A 40 MHz and / or 80 MHz channel can be formed by combining a plurality of consecutive 20 MHz channels. A 160 MHz channel can be formed by combining eight consecutive 20 MHz channels or by combining two non - consecutive 80 MHz channels, which can be referred to as an 80 + 80 configuration. In the case of the 80 + 80 configuration, after channel encoding, the data can pass through a segment parser that can divide the data into two streams. Inverse Fast Fourier Transform (IFFT) processing and time - domain processing can be performed separately on each stream. The streams can be mapped to two 80 MHz channels and the data can be transmitted by the transmitting STA. At the receiver of the receiving STA, the operations described above for the 80 + 80 configuration can be reversed and the combined data can be sent to the Medium Access Control (MAC).

[0046] The sub-1 GHz operating mode is supported by 802.11af and 802.11ah. The channel operating bandwidth and carriers are reduced in 802.11af and 802.11ah compared to those used in 802.11n and 802.11ac. 802.11af supports bandwidths of 5 MHz, 10 MHz, and 20 MHz in the TV White Space (TVWS) spectrum, and 802.11ah supports bandwidths of 1 MHz, 2 MHz, 4 MHz, 8 MHz, and 16 MHz using the non-TVWS spectrum. According to an exemplary embodiment, 802.11ah may support Meter Type Control / Machine-Type Communications (MTC) such as MTC devices in a macro coverage area. The MTC device may have limited capabilities, including certain capabilities, such as support for a certain and / or limited bandwidth (e.g., support only for these). The MTC device may include a battery having a battery life above a threshold (e.g., to maintain a very long battery life).

[0047] A WLAN system that can support multiple channels and channel bandwidths such as 802.11n, 802.11ac, 802.11af, and 802.11ah includes channels that can be designated as primary channels. The primary channel can have a bandwidth equal to the maximum common operating bandwidth supported by all STAs in the BSS. The bandwidth of the primary channel can be set and / or restricted by an STA from among all STAs operating in a BSS that supports a minimum bandwidth operation mode. In an example of 802.11ah, the primary channel can be 1 MHz wide for an STA (e.g., an MTC type device) that supports the 1 MHz mode (e.g., supports only this) even when the AP and other STAs in the BSS support 2 MHz, 4 MHz, 8 MHz, 16 MHz, and / or other channel bandwidth operation modes. Carrier sensing and / or Network Allocation Vector (NAV) setting can depend on the status of the primary channel. For example, if the primary channel is busy by an STA transmitting to an AP (supporting only the 1 MHz operation mode), all of the available frequency band can be considered busy even if most of the available frequency band is idle.

[0048] In the United States, the available frequency band that can be used by 802.11ah is 902 MHz to 928 MHz. In South Korea, the available frequency band is 917.5 MHz to 923.5 MHz. In Japan, the available frequency band is 916.5 MHz to 927.5 MHz. The total bandwidth available for 802.11ah is 6 MHz to 26 MHz depending on the country code.

[0049] FIG. 1D is a system diagram illustrating RAN 104 and CN 106 according to one embodiment. As described above, RAN 104 can use NR radio technology to communicate with WTRUs 102a, 102b, 102c via air interface 116. RAN 104 can also communicate with CN 106.

[0050] RAN 104 may include gNBs 180a, 180b, and 180c, but it should be understood that RAN 104 may include any number of gNBs while remaining consistent with one embodiment. Each of gNBs 180a, 180b, and 180c may include one or more transceivers for communicating with WTRUs 102a, 102b, and 102c via air interface 116. In one embodiment, gNBs 180a, 180b, and 180c may implement MIMO technology. For example, gNBs 180a and 108b may utilize beamforming to transmit signals to and / or receive signals from gNBs 180a, 180b, and 180c. Thus, gNB 180a may transmit and / or receive radio signals to / from WTRU 102a using, for example, multiple antennas. In one embodiment, gNBs 180a, 180b, and 180c may implement carrier aggregation technology. For example, gNB 180a may transmit multiple component carriers to WTRU 102a (not shown). A subset of these component carriers may be on unlicensed spectrum, while the remaining component carriers may be on licensed spectrum. In one embodiment, gNBs 180a, 180b, and 180c may implement coordinated multi-point (CoMP) technology. For example, WTRU 102a may receive coordinated transmissions from gNB 180a and gNB 180b (and / or gNB 180c).

[0051] WTRU 102a, 102b, and 102c can communicate with gNBs 180a, 180b, and 180c using transmissions associated with scalable numerology. For example, the OFDM symbol interval and / or the OFDM sub-carrier interval can vary for different transmissions, different cells, and / or different portions of the radio transmission spectrum. WTRU 102a, 102b, and 102c can communicate with gNBs 180a, 180b, and 180c using sub-frames or transmission time intervals (TTIs) of various or scalable lengths (e.g., including various numbers of OFDM symbols and / or time durations of varying lengths of absolute time).

[0052] gNBs 180a, 180b, and 180c may be configured to communicate with WTRUs 102a, 102b, and 102c in a stand-alone configuration and / or a non-stand-alone configuration. In a stand-alone configuration, WTRUs 102a, 102b, and 102c may communicate with gNBs 180a, 180b, and 180c without accessing other RANs (e.g., eNodeBs 160a, 160b, 160c, etc.). In a stand-alone configuration, WTRUs 102a, 102b, and 102c may utilize one or more of gNBs 180a, 180b, and 180c as mobility anchor points. In a stand-alone configuration, WTRUs 102a, 102b, and 102c may communicate with gNBs 180a, 180b, and 180c using signals in an unlicensed band. In a non-stand-alone configuration, WTRUs 102a, 102b, and 102c may communicate with and connect to gNBs 180a, 180b, and 180c while also communicating with and connecting to another RAN such as eNodeBs 160a, 160b, and 160c. For example, WTRUs 102a, 102b, and 102c may implement a DC principle for communicating with one or more gNBs 180a, 180b, and 180c and one or more eNodeBs 160a, 160b, and 160c substantially simultaneously. In a non-stand-alone configuration, eNodeBs 160a, 160b, and 160c may function as mobility anchors for WTRUs 102a, 102b, and 102c, and gNBs 180a, 180b, and 180c may provide additional coverage and / or throughput for servicing WTRUs 102a, 102b, and 102c.

[0053] Each of gNBs 180a, 180b, and 180c can be associated with a specific cell (not shown) and can be configured to handle decisions for radio resource management, handover decisions, user scheduling in UL and / or DL, support for network slicing, DC, interaction between NR and E-UTRA, routing of user plane data towards user plane functions (UPFs) 184a, 184b, routing of control plane information towards access and mobility management functions (AMFs) 182a, 182b, etc. As shown in FIG. 1D, gNBs 180a, 180b, and 180c can communicate with each other via the Xn interface.

[0054] CN 106 shown in FIG. 1D can include at least one AMF 182a, 182b, at least one UPF 184a, 184b, at least one session management function (SMF) 183a, 183b, and optionally data networks (DNs) 185a, 185b. Although the foregoing elements are depicted as part of CN 106, it will be understood that any of these elements can be owned and / or operated by entities other than the CN operator.

[0055] AMF 182a and 182b can be connected to one or more of gNBs 180a, 180b, and 180c in RAN 104 via the N2 interface and can function as control nodes. For example, AMF 182a and 182b can perform functions such as user authentication of WTRUs 102a, 102b, and 102c, support for network slicing (e.g., handling of different protocol data unit (PDU) sessions with different requirements), selection of specific SMFs 183a and 183b, management of the registration area, termination of non-access stratum (NAS) signaling, and mobility management. Network slicing can be used by AMF 182a and 182b to customize the CN support for WTRUs 102a, 102b, and 102c based on the type of services utilized by WTRUs 102a, 102b, and 102c. For example, different network slices can be established for different use cases such as services that rely on ultra-reliable low latency (URLLC) access, services that rely on enhanced massive mobile broadband (eMBB) access, services for MTC access, etc. AMF 182a and 182b can provide control plane functions for switching between RAN 104 and other RANs (not shown) that employ other radio technologies such as non-3GPP access technologies like LTE, LTE-A, LTE-A Pro, and / or WiFi.

[0056] SMF183a and 183b can be connected to AMF182a and 182b in CN106 via the N11 interface. SMF183a and 183b can also be connected to UPF184a and 184b in CN106 via the N4 interface. SMF183a and 183b can select and control UPF184a and 184b and configure the routing of traffic through UPF184a and 184b. SMF183a and 183b can perform other functions such as the function of managing and allocating UE IP addresses, the function of managing PDU sessions, the function of implementing policies and controlling QoS, and the function of providing DL data notifications. The PDU session type can be IP-based, non-IP-based, Ethernet-based, etc.

[0057] UPF184a and 184b can be connected to one or more of gNB180a, 180b, and 180c in RAN104 via the N3 interface, thereby providing WTRU102a, 102b, and 102c with access to a packet-switched network such as the Internet 110 to facilitate communication between WTRU102a, 102b, and 102c and IP-corresponding devices. UPF184 and 184b can perform other functions such as packet routing and forwarding, implementation of user plane policies, support for multi-home PDU sessions, processing of user plane QoS, buffering of DL packets, and provision of mobility anchoring.

[0058] CN106 can facilitate communication with other networks. For example, CN106 can include or communicate with an IP gateway (e.g., an IP Multimedia Subsystem (IMS) server) that functions as an interface between CN106 and the PSTN 108. In addition, CN106 can provide access to other network 112 for the WTRUs 102a, 102b, 102c, and the other network 112 can include other wired and / or wireless networks owned and / or operated by other service providers. In one embodiment, the WTRUs 102a, 102b, 102c can be connected to the local DNs 185a, 185b through the UPFs 184a, 184b via an N3 interface to the UPFs 184a, 184b and an N6 interface between the UPFs 184a, 184b and the DNs 185a, 185b.

[0059] In view of FIGS. 1A-1D and the corresponding descriptions of FIGS. 1A-1D, one or more of the functions described herein with respect to one or more of the WTRUs 102a-102d, base stations 114a-114b, eNodeBs 160a-160c, MME 162, SGW 164, PGW 166, gNBs 180a-180c, AMFs 182a-182b, UPFs 184a-184b, SMFs 183a-183b, DNs 185a-185b, and / or any other devices described herein can be performed by one or more emulation devices (not shown). An emulation device can be one or more devices configured to emulate one or more of the functions described herein. For example, an emulation device can be used to test other devices and / or simulate network and / or WTRU functionality.

[0060] An emulation device can be designed to implement one or more tests of other devices in a laboratory environment and / or an operator network environment. For example, one or more emulation devices can perform one or more or all functions while being fully or partially implemented and / or deployed as part of a wired and / or wireless communication network to test other devices within the communication network. One or more emulation devices can perform one or more or all functions while being temporarily implemented / deployed as part of a wired and / or wireless communication network. An emulation device can be directly coupled to another device for the purpose of testing and / or performing tests using over-the-air wireless communication.

[0061] One or more emulation devices can perform one or more functions including all while not being implemented / deployed as part of a wired and / or wireless communication network. For example, an emulation device can be utilized in a test scenario in a test laboratory and / or in a wired and / or wireless communication network that is not deployed (e.g., for testing) to implement tests of one or more components. One or more emulation devices can be test equipment. Direct RF coupling and / or wireless communication via an RF circuit (which can include one or more antennas) can be used by an emulation device to transmit and / or receive data.

[0062] In some cases where signals are transmitted, non-ideal oscillators can generate signals impaired by random phase fluctuations called phase noise (PN). The PN power increases with the square of the carrier frequency, meaning that the PN power increases by 6 dB every time the frequency doubles. Another important factor in phase noise is the way a given frequency is multiplied to reach the required system / carrier frequency. As the multiplication factor and the number of multiplications increase, the phase noise of the resulting carrier frequency increases. Therefore, THz and sub-THz frequencies may be more susceptible to PN problems than lower frequencies. This can be further exacerbated due to the immature oscillator technology currently available for generating such higher frequencies. Multi-carrier waveforms such as Cyclic Prefix-Orthogonal Frequency Division Multiplexing (CP-OFDM) or Discrete Fourier Transform-spread Orthogonal Frequency Division Multiplexing (DFT-s-OFDM) can be particularly vulnerable to PN problems because they disrupt the orthogonality of the sub-carriers and cause inter-carrier interference (ICI).

[0063] Phase noise can lead to several impairments on CP-OFDM and DFT-s-OFDM, such as a common phase error (CPE) that represents a constant phase shift applied to all sub-carriers of a signal, but with small random variations around its value. The CPE has a high correlation of its value in the frequency domain but a low correlation in the time domain due to its unpredictability. Another impairment in CP-OFDM and DFT-s-OFDM can be the ICI term caused by leakage of a sub-carrier to adjacent sub-carriers as a result of loss of orthogonality, thus contaminating the complex amplitude of the sub-carrier with unwanted contributions from adjacent sub-carriers. ICI can be, for example, the result of phase noise variations within a symbol.

[0064] Generally, CPE can be an impairment at millimeter wave frequencies, but at such frequencies, the ICI contribution resulting from phase noise can be ignored by appropriate selection of the subcarrier spacing and the reference symbol. For this reason, industry advancements such as 5G NR or future releases may desire to address CPE impairments and / or take specific measures to compensate for CPE impairments at millimeter wave frequencies or any frequency at which improvements can be achieved using one or more of the techniques disclosed herein.

[0065] Figure 2 illustrates an example of PT-RS signal allocation in CP-OFDM 5G NR for DM-RS configurations type 1 (200) and type 2 (210). The horizontal axis depicts time, and the vertical axis depicts frequency, thereby depicting the theoretical range over which a radio signal can be transmitted in time and / or frequency. In one example, the time increment can be indicated by a symbol, and the frequency increment can be indicated by a subcarrier. The effect of common phase error (CPE) can be addressed by introducing a Phase Tracking Reference Signal (PT-RS) for the purpose of correcting the CPE term in the subcarriers of the received signal. Figure 2 shows an example of the placement of the Phase Tracking Reference Signal (PT-RS) signal in Cyclic Prefix Orthogonal Frequency Division Multiplexing (CP-OFDM) for two Demodulation Reference Signal (DM-RS) configurations, namely configuration type 1 (200) and type 2 (210). CPE compensation may be considered essential in Frequency Range 2 (FR2) in order to guarantee good performance, particularly in higher order modulations. At 220, there is an exemplary legend where a square with lines of both left and right slopes represents PT-RS, a square with a right slope is DM-RS(1), and a square with a vertical line is DM-RS(2) (e.g., two DM-RS each at a different port). In one instance, all blank squares can be either no signal, a data signal, or some other non-RS.

[0066] However, when the carrier frequency is increased towards the sub-THz region, CPE alone may not be sufficient to avoid signal degradation. For this purpose, the sub-carrier spacing can be increased to reduce the impact of ICI, and all relevant OFDM parameters are changed according to different numerologies (e.g., in 5G NR) to handle frequencies from below 1 GHz to millimeter-wave frequencies. However, above a certain carrier frequency, the sub-carrier spacing needs to be large enough that the cyclic prefix can no longer absorb the channel's delay spread, or the reduced symbol duration may exceed the tolerance limit and compromise coverage. This motivates the need to explicitly mitigate phase-noise-induced ICI at sub-THz and THz frequencies.

[0067] ICI can have a deeper impact on CP-OFDM than on DFT-s-OFDM, mainly for one or more reasons, namely, the higher time resolution enabled by the former to track phase-noise variations within a symbol, and / or the additional frequency diversity introduced by the spreading operation. In some cases, the PN at carrier frequencies of 52.6 - 71 GHz (FR2-2 frequencies) can be addressed by new numerologies and PT-RS extensions to better handle it. However, further improvements may still be needed to address the potential gains obtained from new PT-RS designs (e.g., for CP-OFDM or DFT-s-OFDM). In some cases, the block-based PT-RS design can be affected by the channel's coherence bandwidth, and some of its PT-RS blocks may need to be assigned in a clustered form to refine the phase-noise estimate by averaging across the PT-RS blocks, where the separation between clusters is determined by the channel's delay spread. This can be demonstrated by simulations.

[0068] As a result of technological progress, one or more problems may exist in wireless systems related to phase noise (PN). PN is a serious problem at very high frequencies where power increases with the square of the carrier frequency and cannot be avoided solely by front-end design. PN-induced ICI is dominant over CPE at sub-THz frequencies and may be more difficult to compensate for due to loss of orthogonality generated on sub-carriers. Increasing the sub-carrier spacing can partially mitigate phase-noise-induced ICI, but may face limitations above a certain frequency due to insufficient support for channel delay spread from shorter cyclic prefixes and / or loss of coverage from reduced symbol duration. Additionally, it may not be feasible to limit the system to a single very wide sub-carrier spacing for multiple devices with a wide range of capabilities.

[0069] Furthermore, PN degradation may be more severe in CP-OFDM waveforms than in DFT-s-OFDM waveforms, which mainly results from the PT-RS design leading to the estimation granularity based on one CP-OFDM symbol. ICI compensation based solely on receiver entity strategies such as ICI cancellation filters or Wiener filters has limited gains and can introduce significant complexity to the actual receiver entity. For example, such receiver strategies were at an acceptable borderline for FR2-2 systems due to significant CPE compared to ICI contributions. In sub-THz and THz systems, such designs may fail considering the increase in PN along with carrier frequency and inefficiency of higher oscillators. In block-based PT-RS designs, benefits can be obtained from a clustered configuration where multiple PT-RS blocks are utilized to refine PN ICI estimation through averaging across blocks. The number of PT-RS blocks and their relative frequency distances may depend on the channel coherence bandwidth, while the size of each PT-RS block depends on the width of the phase-noise spectral response. Therefore, there may not be a single solution that can address all possible device and channel characteristics.

[0070] In addition, the coexistence of devices with very different capabilities and qualities in the same cell can lead to PT-RS designs based on worst-case scenarios, taking into account the maximum possible phase noise spectral width and the coherence bandwidth of the minimum possible channel. Such designs can lead to significant overhead and resource inefficiencies. The phase noise reduction requirements can vary widely depending on the reliability or performance requirements of the application, and PN compensation schemes that can adapt to different application or device characteristics are not yet available.

[0071] Generally, to address one or more of the problems recognized above, and / or one or more problems that may exist in any wireless system, it is necessary to address the phase noise and / or related aspects of the wireless system. To better address PN-induced ICI impairment in CP-OFDM, by calculating and dividing the channels of the allocated PRBs into appropriate groups sized below the coherence bandwidth, and / or by ensuring frequency-domain cyclic symmetric transmission from the transmitting entity that adds cyclic subcarriers to each group, there can be one or more approaches for PN compensation in which multiple groups of reference symbols are transmitted. Such approaches outline techniques for selecting appropriate numbers and sizes of groups to enable an appropriate level of PN compensation at the receiving entity, and provide various ways to ensure circular symmetry within each group. This approach may also include helping the receiving entity reduce phase noise by mapping complex data symbols and reference signals to subcarriers within the frequency-domain groups to better adapt to transceiver characteristics and channel conditions.

[0072] For purposes of explanation, in this specification, it may be assumed that a CP-OFDM symbol is scheduled for the transmission of one or several frequency-division multiplexed signals in a wireless communication system affected by phase noise. The transmission to / from any given user (e.g., for a given device) is the M allocated to it awill include a number of sub-carriers. In the downlink of such a wireless communication system, the transmitted signal can address multiple users each including a different number of allocated sub-carriers sharing the same time resource via frequency multiplexing or spatial multiplexing of complex modulation symbols. In the uplink, the transmitted signal corresponding to a given user can be assumed to include M a allocated sub-carriers. The total system bandwidth will include N sub-carriers corresponding to the size of the discrete Fourier transform (DFT) or fast Fourier transform (FFT) required to switch between the time domain and the frequency domain.

[0073] Phase noise impairment is a randomly varying constant envelope multiplicative noise term e that affects the time domain samples x[n] for each CP-OFDM symbol and can be regarded as jθ[n] The signal impaired by phase noise can be written in the following form assuming no other impairments from either the channel or the transceiver.

[0074]

Number

[0075]

Number

[0076]

Number

[0077]

Number

[0078] However, if the allocated bandwidth is further divided into L sub-carrier groups each of length M, and each group exhibits circularity in the frequency domain, the same convolution property can be retained in each sub-carrier group as follows.

[0079]

Number

[0080] Using one or more of the above equations for the analysis of the phase noise impairment can have one or more advantages such as being able to separately process the sub-carrier groups, estimating and further compensating for the phase noise ICI by using smaller DFTs for each sub-carrier group, and thus reducing the overall complexity.

[0081] When using one or more of the above equations for the analysis of phase noise impairment, there may be one or more advantages, such as that PN compensation is typically performed by the receiving entity after channel equalization. Thus, considering that the residual equalization error can vary in each subcarrier group depending on the value of the coherence bandwidth of the channel, it is desirable to estimate the phase noise separately in each subcarrier group in order to avoid the influence of residual errors from another frequency domain having a very different channel response. Further averaging of the estimated values across subcarrier groups can lead to an improvement in frequency diversity in the PN compensation process. The size M of the subcarrier group should be below the coherence bandwidth of the channel in order to benefit from frequency diversity when averaging the estimated values across the subcarrier group. The coherence bandwidth of the channel can be assumed to be known via channel state information (CSI) feedback or direct estimation by the transmitting entity when channel reciprocity is guaranteed (such as in a Time Division Duplex (TDD) system that uses the same carrier frequency for uplink and downlink).

[0082] When using one or more of the above equations for the analysis of phase noise impairment, there may be one or more advantages, such as that CPE estimation can potentially utilize the presence of legacy PT-RS signals inserted in the bandwidth allocated to the WTRU. When PN-induced ICI is significant, the PT-RS signals can be assumed to be present in all CP-OFDM symbols in order to track CPE variations due to the low temporal coherence of the phase noise.

[0083] Signals in the frequency domain can generally be non-cyclic unless a suitable frequency domain cyclic structure is added to the end or beginning of a subcarrier group either as a cyclic prefix or a cyclic suffix (or both), resulting in the cyclic partitioning method shown in this specification such as in Figure 3.

[0084] Figure 3 illustrates an example of cyclic division where frequency 350 is shown on the horizontal axis. 300 has M a sub-carriers 301 of the allocated bandwidth of the WTRU having non-limiting examples of signals (e.g., PT-RS 302, DM-RS 303, PDSCH / PUSCH 304). Moving 309 to the bottom of the figure, at 310, a frequency domain cyclic prefix / suffix (FD-CP, FD-CS) structure is added at the beginning and end respectively to each of them (e.g., FD-CP 314, FD-CS 315), M a cyclic division of the L sub-carrier groups (e.g., sub-carrier group #0 311 to sub-carrier group #L-1 312) of the M sub-carriers 301 (e.g., the allocated bandwidth of the WTRU) may exist. Details of FD-CP / CS insertion in each sub-carrier group are illustrated in Figure 4.

[0085] Figure 4 illustrates an example of FD-CP / CS insertion in a sub-carrier group. As shown by 400, there is an I-th group of sub-carriers 412 with frequency 450 shown on the horizontal axis. For maximum generality, a frequency domain cyclic prefix (FD-CP) 414 and / or a frequency domain cyclic suffix (FD-CS) 415 may be added at the beginning / end to the sub-carrier group to achieve signal circulation. The signal within the sub-carrier can be data, PT-RS, DM-RS, etc. (e.g., 419). In an actual situation, any one of one FD-CP, one FD-CS, or a combined FD-CP / CS may be preferred. The FD-CP may include the last L CP sub-carriers within the sub-carrier group, and the FD-CS may include a replication of the first L CS sub-carriers within the sub-carrier group. The sub-carrier group size M may be below the coherence bandwidth B coh of the channel. The length L of the frequency domain cyclic prefix CP416, and the length L of the frequency domain cyclic suffix CS 417 can be greater than or equal to a function of the phase noise spectral width.

[0086] FIG. 5 illustrates an example of a phase noise response showing the one-sided spectral width with respect to the -120 dBc / Hz power spectral density. As shown at 500, the frequency is shown on the horizontal axis 550 and the phase noise is shown on the vertical axis 551. L CP and L CS Both can be related to the one-sided or both-sided spectral width of the phase noise response observed over the entire transmit-receive transceiver chain shown in FIG. 5, as described in the following subsections. Δf PN can indicate the one-sided spectral width of the phase noise for a given level, and thus the two-sided spectral width of the phase noise can be 2Δf PN For the sake of simplicity and without intending to limit any disclosure, only the relative values of Δf PN and 2Δf PN can be considered with respect to the subcarrier spacing.

[0087] In FIGS. 6, 7, and 8, the horizontal axis shows the frequency. M can represent the region size (e.g., 613, 713, and 813).

[0088] FIG. 6 illustrates an example of a single FD-CP insertion for each subcarrier group. In this case, a single FD-CP 614 having a size L CP ≧2Δf PN can circularize the subcarrier group, as shown in the example of FIG. 6. The subcarriers (including the trailing shaded region) in the region of size M of 613 can include data, PT-RS, DM-RS (e.g., 619), or any other control / data signal that is expected to be mapped therein. In some cases, the length L CP 616 can be small on the order of less than a factor of 10 even at very high frequencies. CPE can correspond to the DC component of P[k] such as P[0].

[0089] To handle both the positive and negative frequency shifts caused by phase noise in the sub - carrier group, the DFT window 661 for PN compensation starts at the center of the FD - CP 614 and ends before the end of the CP - OFDM symbol by sub - carrier Δf PN Assuming this, the control / data sub - carriers originally scheduled within the sub - carrier group are L CP / 2 sub - carriers that can be cyclically shifted to the right (e.g., see the arrow) within the DFT window, which can be taken into account by the phase - noise compensation algorithm.

[0090] Figure 7 illustrates an example of the insertion of a single - frequency - domain cyclic suffix (FD - CS) 715 for each sub - carrier group. In this case, the frequency - domain cyclic suffix FD - CS 715 can play the same role as the FD - CP shown in Figure 6 (e.g., the same explanations in Figure 6 apply to Figure 7). The size of the FD - CS 715 must satisfy the condition L CS ≧2Δf PN to achieve circulation, and the control / data sub - carriers 719 originally scheduled in the sub - carrier group are L CP / 2 sub - carriers that can be cyclically shifted to the left (e.g., see the arrow) within the DFT window.

[0091] The advantage of using a single FD - CP or FD - CS is its similarity to the already known CP - insertion techniques employed in CP - OFDM, at the expense of a cyclic shift of half the length of the FD - CP or FD - CS in the control / data information contained in the DFT window (e.g., 661, 761). However, since PN compensation is performed after channel equalization, in some cases, this shift may not affect performance as long as the PN compensation takes into account the correct sub - carrier ordering.

[0092] Figure 8 illustrates an example of combined FD-CP / CS insertion for each sub-carrier group. This includes the more general case where both FD-CP 814 and FD-CS 815 are added to the end and to the beginning, respectively, of a sub-carrier group (e.g., M 813) as shown in Figure 8. Assuming a symmetric phase noise response, FD-CP / CS must satisfy the condition L CP =L CS ≧Δf PN The advantage in this case is that no reordering is required when performing PN compensation in each sub-carrier group and the DFT window 861 includes the original sub-carriers without shift.

[0093] Without loss of generality, the embodiments disclosed herein may relate to the general insertion of FD-CP / CS into sub-carrier groups corresponding to either a single FD-CP, a single FD-CS, or a combined FD-CP / CS, depending on the implementation. The lengths and sizes M of FD-CP and FD-CS may be adapted for each WTRU to phase noise and channel conditions in the relevant part of the carrier bandwidth.

[0094] The one-sided or two-sided spectral width of the phase noise may be either determined in advance by the transceiver or reported by the receiving entity. The phase noise spectral width generally indicates the combined PN characteristics of the transmitter entity oscillator and the receiver entity oscillator.

[0095] FIG. 9 illustrates an example of a transmission process for generating a CP-OFDM signal based on phase noise cyclic division. To illustrate one or more of the techniques disclosed herein, a process for the transmission of a CP-OFDM signal based on phase noise cyclic division can be illustrated in the example of FIG. 9. The normal (e.g., legacy) processing for the generation of a CP-OFDM signal can be depicted by shaded blocks (e.g., 921), while new or modified blocks can be depicted by unshaded blocks (e.g., 922). The transmission steps can focus on the generation of a CP-OFDM signal for a given WTRU, but all explanations can be extended to the case of multiple WTRUs frequency multiplexed within the same CP-OFDM symbol. Transmission can also be based on a single transmit-receive point (TRP), but the techniques disclosed herein can be applied when having multiple TRPs as illustrated herein. As discussed herein, one or more TRPs can be part of a base station.

[0096] As disclosed herein (e.g., below), there can be techniques in the processing steps required for the generation of a CP-OFDM symbol based on the disclosed embodiments of the phase noise cyclic division method described herein.

[0097] As shown in FIG. 9, data bits proceed to FEC encoding 901 and may deliver one or more symbols. In one example, each symbol is processed individually. In the case of FD-CP / CS / M selection 902, this block performs a selection of the length of the FD-CP and / or FD-CS fields as well as the size M of the subcarrier group. The FD-CP / CS / M selection can follow the guidelines described herein (e.g., the phase noise cyclic division method), i.e., M can be less than or equal to the coherence bandwidth of the channel experienced by the WTRU, and the length of the FD-CP and / or FD-CS should follow any of the criteria described herein in this or other examples (e.g., single FD-CP insertion per subcarrier group, single FD-CS insertion per subcarrier group, combined FD-CP / CS insertion per subcarrier group). If the coherence bandwidth of the channel is greater than the allocated bandwidth of the WTRU, the transmitting entity may decide not to perform phase noise cyclic division as the benefit of having FD-CP or FD-CS would be lost in this case (e.g., the receiving entity may perform ICI compensation based on a particular implementation without any need for changes to the transmitted signal). Otherwise, the block distributes the number of subcarrier groups, its size M, and the length of the FD-CP and / or FD-CS fields for use by the transmitting entity.

[0098] The value of M and the length of the FD-CP and / or FD-CS can be selected from among the allowed combinations in a pre-defined codebook of pre-defined values that can be pre-known to the transmitting and receiving entities to appropriately handle any expected phase noise characteristics and channel coherence bandwidth.

[0099] The factors governing phase noise can be the quality of the oscillators in the transmitting and receiving devices. In some cases, this factor can be important relative to other factors, as disclosed herein. More precisely, the oscillators, phase-locked loops, and the overall process of carrier generation can potentially affect phase noise, but for the sake of explanation, the term oscillator quality is being used. The transmitting entity may have knowledge of its oscillator quality, but may not have information regarding the receiving entity oscillator. In some cases, knowledge of the actual oscillator quality causes the transmitting entity to appropriately select a parameter set for PN compensation to achieve a trade-off between overhead and performance, but there may be some minimum requirements to be met.

[0100] The selection can be based on channel state information of the transmit-receive link and / or any known PN information, including, for example, the PN spectral width or PN capabilities of the receiving entity. The PN information can be obtained from a feedback report sent by the receiving entity, or through measurements performed by the transmitting entity on signals received from peer nodes in the opposite link direction, such as when the receiving entity is operating as a transmitting entity. Assuming that the PN is the result of combined impairments from the transmit and receive radio frequency chains, it may be possible to infer its characteristics in either the downlink or uplink, on the condition that the same pair of transmit / receive nodes is considered in each case.

[0101] The rules for the selection of FD-CP / CS / M can be based on semi-static PN configuration messages received by upper layer signaling, or can depend on the received feedback, and / or can be based on dynamic policies triggered by specific events previously configured by upper layer signaling. The selection can also take into account the overhead introduced by the FD-CP / CS field in order to minimize its impact on the available resources.

[0102] To better respond to the phase noise experienced by the receiving entity, the transmitting entity may take into account an instruction received from a peer entity that notifies of high phase noise at reception, which may trigger an increase in FD-CP and / or FD-CS length, for example, to better absorb ICI. Such an instruction may be sent by the receiving entity in an uplink shared control or data channel (e.g., 5G NR PUCCH or PUSCH), or using a Medium Access Control (MAC) control element (CE), a MAC CE. The instruction may be based on the phase noise ICI power exceeding a threshold configured by the transmitting entity via upper layer signaling or in a phase noise configuration message, for example, in a downlink shared control or data channel (e.g., PDCCH or PDSCH), or using a MAC CE.

[0103] CSI information may include any indication of channel quality measured by the receiving entity and reported to the transmitting entity, such as channel quality indicator (CQI) information per frequency sub-band, signal-to-noise ratio (SNR), or an explicit measurement of the coherence bandwidth of the channel. CSI may also be obtained by the transmitting entity from measurements performed in the opposite link direction when the channel correlation conditions are met (e.g., when the downlink carrier frequency and the uplink carrier frequency are the same, as in a TDD system).

[0104] PN information can include, but is not limited to, any of the following metrics in any suitable unit or according to any predefined quantization scale: Indications of the represented phase noise spectral width (e.g., in Hz or number of sub-carriers); an indication representing the number of non-ignorable ICI coefficients that describe the phase noise under current operating conditions; the power of the experienced phase noise impairment; an indication of the post-detection SNR measured at the receiving entity after equalization and phase noise compensation; the residual mean-squared error (MSE) of detection at the output of the phase noise compensation algorithm; and / or the error vector magnitude (EVM) of the constellation seen at the receiving entity after equalization.

[0105] Without departing from the concepts contained in the examples provided herein, other measurements may also be contemplated.

[0106] Any PN information reported by the receiving entity may be sent in a periodic, semi-periodic, on-demand, or event-triggered manner. Some of the above PN information may be inferred by the transmitting entity from measurements performed in the opposite link direction, such as the phase noise spectral width or the number of non-ignorable ICI coefficients that describe the phase noise.

[0107] Information regarding the PN capabilities of the receiving entity may be obtained by feedback sent by the receiving entity node at session establishment. The PN capabilities may include, for example, a radio frequency category or oscillator quality class, or an indication of the amount of phase noise that the receiving device is expected to experience under typical operating conditions (e.g., temperature, power, or cell load) as measured by the phase noise spectral width, the number of non-ignorable ICI coefficients that characterize the phase noise for a given numerology or set of numerologies, or any other similar information. The PN capabilities may also be obtained from upper layer signaling in a static or dynamic manner according to application requirements, or retrieved from a database that stores the phase noise characteristics of the receiving entity.

[0108] The rate matching block 903 of the example shown in FIG. 9 obtains the selected values of L CP , L CS , and M from the FD-CP / CS / M selection block 902, and after considering the overhead introduced by FD-CP and / or FD-CS, together with the overhead introduced by any other control and reference signals, o = (L CP +L CS ) / M can be calculated to adjust the net amount of data information that can be mapped to subcarriers. The rate matching block can operate after the forward error correction (FEC) coding block 901, which is intended to provide redundancy to the information for improved resilience against channel impairments, and adjusts the amount of parity information in its output to match the available physical resources in the CP-OFDM symbol.

[0109] After modulating the rate-matched data bits into complex constellation symbols (904) and performing serial-to-parallel (S / P) conversion (905), the subcarrier splitting block 906 can receive as inputs complex control symbols and complex data symbols mapped onto the physical resources, and split the entire set of size M a into one or more subcarrier groups, each of length M. The control signals and reference signals are included, for example, in the useful part of the subcarrier group of length M, including PT-RS and / or DM-RS derived from 5G NR. Subsequently, the FD-CP 907 and FD-CS 909 fields, each containing a copy of the last or first complex symbol, can be added to the beginning or end of each subcarrier group to maintain circularity in the frequency domain and enable DFT-based PN compensation for each subcarrier group.

[0110] The remaining steps for transmission are the time-domain signal s TInverse FFT of size N for generating [n], parallel-serial (P / S) conversion 910, and / or addition of a time-domain cyclic prefix to absorb multipaths caused by channel delay spread, thus providing signal circularity in the time domain may be included.

[0111] The transmitting entity may signal to the receiving entity the indication of the length used for FD-CP and / or FD-CS, and the value of M employed in one or several consecutive CP-OFDM symbols 912. A single FD-CP / CS / M indication including the required parameters may be sent, or depending on the implementation mode, several separate indications may also include the corresponding parameters. The transmitting entity may send an index corresponding to a pre-defined codebook including all possible combinations of the FD-CP length and / or FD-CS length and the value of M so that the receiving entity can clearly obtain the selected parameters 912. Blind detection of these parameters may also be possible by the receiving entity to avoid explicit signaling of these parameters.

[0112] In a compatible design, the network can configure a mapping table where each row provides an appropriate combination of parameter sets, i.e., the lengths of FD-CP / CS / M. The network selects an appropriate configuration for PN compensation at the receiving entity and indicates the row index to the WTRU. The pre-configuration may indicate to the WTRU whether the indication for the PN parameter set is dynamic or static. In the dynamic case, the indication of the selected configuration can be transmitted in each DCI that provides a lot of flexibility and reactivity for adapting to the system and transmission parameters. In the static or semi-static case, the PN parameter set indication can be provided as part of radio resource control (RRC) signaling or MAC-CE.

[0113] The same mechanism and mapping structure can be used by a WTRU to provide feedback to the network as to which parameter set it wants to receive for its PN compensation. The WTRU may provide an indication of its desired PN parameter set as part of upper layer signaling.

[0114] The signaling indication may be sent periodically, semi-periodically, on demand, or triggered by an event such as a change in the coherence bandwidth of the channel or when the phase noise condition in the transmit-receive chain substantially changes.

[0115] FIG. 10 illustrates an exemplary process for receiving a CP-OFDM signal based on phase noise cyclic division. The processing steps for receiving a CP-OFDM signal based on phase noise cyclic division may be illustrated in FIG. 10. Without loss of generality, reception of a signal from a single TRP may be assumed, but the description can be readily applied to the case of multiple TRPs as described herein. The receiving steps may be focused on a given WTRU, but all descriptions can be readily extended to the case of multiple WTRUs frequency multiplexed within the same CP-OFDM symbol. In the example of FIG. 10, note that the normal (e.g., legacy) processing of the signal may be depicted by shaded blocks (e.g., 1021), while the new or changed blocks may be depicted by unshaded blocks (e.g., 1022).

[0116] After a symbol is received 1001, serial-to-parallel conversion 1002 and an N-point FFT 1003 are performed, the received symbol may be equalized after channel estimation 1004 assisted by a DM-RS signal (e.g., in 5G NR). Then, CPE compensation 1005 may be performed assisted by, for example, a PT-RS signal in 5G NR, and the subcarriers may be de-interleaved 1006 by concatenating M subcarrier groups and removing the FD-CP and / or FD-CS fields. Length L CP 、L CSAnd M can be assumed to be obtained from signaling from the transmitting entity side, via upper layer indications, or through blind detection. Signaling from the transmitting entity can refer to a pre-defined codebook that includes all possible combinations of the FD-CP length and / or FD-CS length and the value of M so that the receiving entity can clearly obtain the selected parameters.

[0117] At the output of this block, the content of the M useful sub-carriers within each sub-carrier group can be distributed to the PN ICI removal block 1007 for ICI compensation.

[0118] Regarding the phase noise ICI removal block 1007, this block can perform the estimation and subsequent removal of the phase noise ICI impairment individually for each sub-carrier group, and utilize signal recycling by further averaging across the sub-carrier groups for additional frequency diversity. Measurement of the residual phase noise power after the ICI removal process can be performed, for example, to evaluate whether there is high phase noise so that the transmitting entity can perform correction actions to further reduce the phase noise. For example, if the residual phase noise power exceeds a threshold, the receiving entity can signal the high phase noise and send an indication containing some phase noise related information to the transmitting entity, such as the phase noise spectral width, the number of non-ignorable ICI coefficients of the phase noise response, the detected SNR, the residual MSE of the detection after ICI mitigation, the EVM of the constellation after equalization, and / or the like.

[0119] As an example of the ICI removal algorithm, there can be one or more steps that can be followed by the receiving entity to perform PN-induced ICI compensation.

[0120] First, the device performs equalization and CPE compensation of the received signal to obtain complex symbols in the frequency domain

[0121]

Number

[0122] Second, the device obtains the values of L CP , L CS , and M via signaling or blind detection, obtains the l-th group of M sub-carriers, and the symbols within the l-th sub-carrier group

[0123]

Number

[0124]

Number

[0125] Third, assuming that the l-th sub-carrier group symbols

[0126]

Number

[0127]

Number

[0128]

Number

[0129]

Number

[0130]

Number

[0131]

Number

[0132]

Number

[0133]

Number

[0134]

Number

[0135] Fourthly, the second and third steps are repeated for each subcarrier group, and after restoring the residual CPE that may remain after equalization, the ICI coefficients in all subcarrier groups are averaged and its size is extended to N, thus obtaining the following.

[0136]

Number

[0137]

Number

[0138] Fifthly, the device

[0139]

Number

[0140]

Number

[0141]

Number

[0142] The foregoing exemplary process is merely an example of an ICI compensation algorithm, and there are other possibilities depending on the implementation. Its complexity C deICI is measured as the number of complex multiplications and can be given by the following.

[0143]

Number

[0144] [Number] is the complexity of f QAM and represents.

[0145] As shown in the example of FIG. 10, after the parallel-serial conversion 1008 and demodulation 1009 of the subcarrier data, the rate matching operation performed during transmission can be reversed 1010 to restore the original bits. The rate matching operation can be assisted by an indication of length L CP , L CS , and M obtained via signaling to a remote entity, upper layer signaling, or blind detection. The output of this block 1010 includes the received coded bits that are FEC decoded 1011 to recover the original information bits (e.g., data bits).

[0146] In addition to CSI information, the receiving entity may report to the transmitting entity information regarding the amount of phase noise experienced in detection, including, for example, several phase noise-related metrics such as an indication of high phase noise conditions, e.g., phase noise spectral width, the number of non-ignorable ICI coefficients of the phase noise response, the detected SNR, or the residual MSE of the detection, and a phase noise capability report. These metrics can be sent periodically, semi-periodically, on demand, or event-triggered. The event-triggered type of report can be based on one or several conditions to be met during reception, such as the residual phase noise ICI power exceeding a predetermined threshold, and can be configured in an upper layer signaling or in a phase noise configuration information message sent by the transmitting entity. Periodic, semi-periodic, or on-demand reports can also be based on the phase noise configuration received via upper layer signaling or the phase noise configuration in the phase noise configuration information message sent by the transmitting entity.

[0147] The phase noise capabilities of the receiving entity may include, for example, an indication of the amount of phase noise expected to be experienced under typical operating conditions (e.g., temperature, power, or cell load) as measured by, for example, a radio frequency category or oscillator quality class, or phase noise spectral width, the number of non - negligible ICI coefficients characterizing the phase noise for a given numerology or set of numerologies, or any other similar information.

[0148] FIG. 11 illustrates an exemplary procedure for transmitting a CP - OFDM symbol based on phase - noise cyclic division. In the exemplary method shown, a first WTRU or set of WTRUs transmitting a CP - OFDM symbol to a second WTRU or set of second WTRUs may perform one or more of the following: At 1101, obtaining phase - noise information (e.g., phase - noise capabilities or phase - noise spectral width Δf PN ) characterizing the amount of phase noise experienced on the communication link; at 1102, determining the coherence bandwidth B coh of the channel; at 1103, based on B coh and the phase - noise information, selecting a default value M for the sub - carrier group size, a length L CP for the frequency - domain cyclic prefix, and a length L CS for the frequency - domain cyclic suffix; at 1104, if the coherence bandwidth of the channel is lower than the allocated bandwidth of the WTRU, adapting the cyclic - division parameters M, L CP , and L CS to the instantaneous conditions, and / or at 1105, determining whether a high - phase - noise indication is reported by the second WTRU; at 1106, based on the high - phase - noise indication received from the second WTRU (e.g., if 1104 and 1105 are "yes"), L CP and L CSUpdating the value of; at 1107, executing a rate matching function to adjust the amount of data mapped to available physical resources after considering the frequency domain cyclic prefix field and / or the frequency domain cyclic suffix field; at 1108, dividing subcarriers into M subcarrier groups and appending / prepending a frequency domain cyclic prefix and / or a frequency domain cyclic suffix to each subcarrier group; at 1109, M, L CP and L CS Sending signaling information including values such as; and / or, at 1110, transmitting a CP-OFDM symbol. At 1104, if the result is "no", at 1111, executing the rate matching function without considering any overhead from cyclic partitioning; at 1112, mapping information to subcarriers without cyclic partitioning and then proceeding to 1109 and transmitting the signaling information as disclosed herein. At 1105, in the absence of a high PN indication, the WTRU proceeds directly to executing the rate matching function at 1107.

[0149] (For example, with respect to any figure, description, or example in this specification such as Figures 11, 12, 13, etc.) In one example of the transmission procedure described herein, phase noise information may be obtained / sent via upper layer signaling (e.g., via RRC phase noise configuration information).

[0150] (For example, with respect to any figure, description, or example in this specification such as Figures 11, 12, 13, etc.) In one example of the transmission procedure described herein, phase noise information may be obtained from an indication transmitted by a second WTRU via, for example, an uplink shared control or data channel (e.g., PUCCH or PUSCH), or using MAC CE.

[0151] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, phase noise information can be obtained by the first WTRU or set of first WTRUs by measuring the amount of phase noise experienced in the opposite link direction between the first WTRU or set of first WTRUs and the second WTRU or set of second WTRUs.

[0152] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, phase noise information can include an indication from the second WTRU or set of second WTRUs that includes the length of the frequency domain cyclic prefix and the length of the frequency domain cyclic suffix, and the subcarrier group size, which are employed by the first WTRU or set of first WTRUs in the next CP - OFDM symbol or set of CP - OFDM symbols.

[0153] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, phase noise information can include an indication from the second WTRU or set of second WTRUs that includes a preferred subcarrier partition by an index to a codebook of a priori - defined combinations of the length of the frequency domain cyclic prefix and the length of the frequency domain cyclic suffix, and the subcarrier group size, which are known to the first WTRU or set of first WTRUs and the second WTRU or set of second WTRUs.

[0154] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, phase noise capabilities can include an indication of a priori - known radio frequency category or oscillator quality class from a set of a priori categories or classes, or an indication of the amount of phase noise experienced in typical operating conditions (e.g., temperature, power, and / or cell load).

[0155] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise can be expressed as the phase noise spectral width measured in units of Hz or number of subcarriers for a given numerology or set of numerologies.

[0156] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise can be expressed as the number of non - negligible ICI coefficients in the phase noise spectral response under current operating conditions.

[0157] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise can be expressed as the power of the experienced phase noise impairment in watts, milliwatts, dBW, dBm, or any other suitable unit.

[0158] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise can be expressed as an indication of the post - detection signal - to - noise ratio measured at the receiving entity after equalization and phase noise compensation.

[0159] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise can be expressed as the residual mean - square error of detection at the output of the phase noise compensation algorithm.

[0160] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise can be expressed as the magnitude of the error vector of the constellation seen at the receiving entity after equalization.

[0161] (For example, with respect to any figure, description, or example in this specification such as Figures 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the high phase noise indication may be reported by a second WTRU in an uplink shared control or data channel (e.g., PUCCH or PUSCH), or using a MAC CE.

[0162] (For example, with respect to any figure, description, or example in this specification such as Figures 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the high phase noise indication may be reported by a second WTRU based on a phase noise threshold transmitted by a first WTRU or a set of first WTRUs in a phase noise configuration message (e.g., in a downlink shared control or data channel, PDCCH or PDSCH, or using a MAC CE).

[0163] (For example, with respect to any figure, description, or example in this specification such as Figures 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the coherence bandwidth of the channel may be obtained from a channel state information indication reported by a second WTRU, or may be measured by a first WTRU or a set of first WTRUs on a signal received from a second WTRU when the uplink and downlink carrier frequencies are the same.

[0164] (For example, with respect to any figure, description, or example in this specification such as Figures 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the subcarrier group size M may be less than or equal to the coherence bandwidth of the channel.

[0165] (For example, with respect to any figure, description, or example in this specification such as Figures 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the frequency domain cyclic prefix is the last L CP replications of the complex subcarrier amplitudes within each subcarrier group added at the beginning to provide circularity of the signal in the frequency domain.

[0166] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the frequency domain cyclic suffix is the first L within each subcarrier group added at the end to provide circularity of the signal in the frequency domain CS including a replication of the complex subcarrier amplitudes of the first L.

[0167] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the length of the frequency domain cyclic prefix can be 0, and the length of the frequency domain cyclic suffix can be equal to the two-sided phase noise spectral width represented by the number of subcarriers.

[0168] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the length of the frequency domain cyclic suffix can be 0, and the length of the frequency domain cyclic prefix can be equal to the two-sided phase noise spectral width represented by the number of subcarriers.

[0169] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, both the length of the frequency domain cyclic prefix and the length of the frequency domain cyclic suffix can be equal to the one-sided phase noise spectral width represented by the number of subcarriers.

[0170] (For example, with respect to any figure, description, or embodiment of this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, when calculating the amount of data information after forward error correction coding that can be mapped to physical available resources, the rate matching function may consider the overhead caused by the frequency domain cyclic prefix and / or the frequency domain cyclic suffix.

[0171] (For example, with respect to any figure, description, or embodiment of this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the signaling information may include an indication of the length of the frequency domain cyclic prefix and the length of the frequency domain cyclic suffix, and the subcarrier group size, which are adopted in the next CP - OFDM symbol or a set of CP - OFDM symbols.

[0172] (For example, with respect to any figure, description, or embodiment of this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the signaling information may include an index to a codebook of a priori defined combinations of the length of the frequency domain cyclic prefix and the length of the frequency domain cyclic suffix, and the subcarrier group size, which must be known to the first WTRU or a set of first WTRUs and the second WTRU or a set of second WTRUs for clear detection.

[0173] (For example, with respect to any figure, description, or embodiment of this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the signaling information may be obtained via upper layer signaling or may be sent by the first WTRU or a set of first WTRUs in a periodic, semi - periodic, on - demand, or event - based manner using periodicity and received from the second WTRU or a set of second WTRUs in a phase noise configuration message via (for example, downlink shared control or data channel, PDCCH or PDSCH, or MAC CE).

[0174] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, an event for triggering signaling information may be based on, for example, a variation in the coherence bandwidth of a channel exceeding a first threshold, or a variation in the phase noise spectral width exceeding a second threshold.

[0175] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, in the downlink of a wireless communication system, the first WTRU is a base station device, and the second WTRU is a UE.

[0176] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the set of first WTRUs are a plurality of transmit-receive points in the downlink of a multi-TRP wireless communication system.

[0177] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the first WTRU and the second WTRU are UEs in the sidelink of a wireless communication system.

[0178] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, in the uplink of a wireless communication system, the first WTRU is a UE, and the second WTRU is a base station device.

[0179] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the set of second WTRUs are a plurality of transmit-receive points in the uplink of a multi-TRP wireless communication system.

[0180] FIG. 12 illustrates an exemplary procedure for the transmission of a CP - OFDM symbol based on phase noise cyclic division. In this embodiment, a first WTRU or a set of first WTRUs transmitting a CP - OFDM symbol to a second WTRU or a set of second WTRUs may perform one or more of the following: First, at 1201, the first WTRU may obtain / select default phase noise mitigation parameters (e.g., of M, L CP and L CS ); at 1202, the first WTRU may start one or more transmissions to one or more second WTRUs based on the selection of default phase noise mitigation parameters such as the default value M of the sub - carrier group size, the length L of the frequency - domain cyclic prefix CP and the length L of the frequency - domain cyclic suffix CS ; at 1203, the first WTRU may receive a phase noise report from the second WTRU that includes either a high - phase noise indication and / or an indication of the coherence bandwidth of a channel lower than the allocated bandwidth of the second WTRU; at 1204, the first WTRU may adapt the cyclic division parameters M, L CP , and L CS to the instantaneous conditions based on the received phase noise report (e.g., high - phase noise indication) from the second WTRU; at 1205, the first WTRU may perform a rate - matching function, divide the sub - carriers into M sub - carrier groups, and append / add a frequency - domain cyclic suffix / prefix to the end / beginning of each sub - carrier group; at 1206, the first WTRU may transmit updated parameters, such as by sending signaling information including parameters such as the values of M, L CP and L CS ; and / or, at 1207, the first WTRU may transmit a CP - OFDM symbol based on the updated phase noise mitigation parameters.

[0181] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the phase noise report may include an indication from a second WTRU or a set of second WTRUs, including the length of the frequency domain cyclic prefix and the length of the frequency domain cyclic suffix, and the subcarrier group size, which is adopted by a first WTRU or a set of first WTRUs in the next CP-OFDM symbol or set of CP-OFDM symbols.

[0182] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the phase noise report may include an indication from a second WTRU or a set of second WTRUs, including a preferred subcarrier partition, by an index to a codebook of an empirically defined combination of the length of the frequency domain cyclic prefix and the length of the frequency domain cyclic suffix, and the subcarrier group size, which is known to a first WTRU or a set of first WTRUs and a second WTRU or a set of second WTRUs.

[0183] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the high phase noise indication may be reported by a second WTRU in an uplink control or shared data channel (e.g., PUCCH or PUSCH), or using a MAC CE.

[0184] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the high phase noise indication may be reported by a second WTRU based on a phase noise threshold transmitted by a first WTRU or a set of first WTRUs in a downlink control or shared data channel, a phase noise configuration message such as PDCCH or PDSCH, or using a MAC CE.

[0185] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the subcarrier group size M can be less than or equal to the coherence bandwidth of the channel.

[0186] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the frequency domain cyclic prefix is the replication of the complex values associated with the last L subcarriers in each subcarrier group added at the beginning to provide circularity of the signal in the frequency domain. CP It includes the replication of complex values associated with the last L subcarriers in each subcarrier group added at the beginning to provide circularity of the signal in the frequency domain.

[0187] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the frequency domain cyclic suffix is the replication of the complex values associated with the first L subcarriers in each subcarrier group added at the end to provide circularity of the signal in the frequency domain. CS It includes the replication of complex values associated with the first L subcarriers in each subcarrier group added at the end to provide circularity of the signal in the frequency domain.

[0188] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the length of the frequency domain cyclic prefix can be 0, and the length of the frequency domain cyclic suffix can be equal to the two-sided phase noise spectral width represented by the number of subcarriers.

[0189] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the length of the frequency domain cyclic suffix can be 0, and the length of the frequency domain cyclic prefix can be equal to the two-sided phase noise spectral width represented by the number of subcarriers.

[0190] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, both the length of the frequency domain cyclic prefix and the length of the frequency domain cyclic suffix can be made equal to the one-sided phase noise spectrum width represented by the number of subcarriers.

[0191] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the rate matching function is to adjust the amount of data mapped to the available physical resources after considering the frequency domain cyclic prefix field and / or the frequency domain cyclic suffix field.

[0192] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the first WTRU or the set of first WTRUs transmits control signaling information including any one of an indication of adaptation of the phase noise mitigation parameter, an updated value of the subcarrier group size (M), an updated value of the length of the frequency domain cyclic prefix (L CP ), and an updated value of the length of the frequency domain cyclic suffix (L CS ).

[0193] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, in the downlink of a wireless communication system, the first WTRU is a base station device and the second WTRU is a UE.

[0194] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the set of first WTRUs are a plurality of transmission and reception points in the downlink of a multi-TRP wireless communication system.

[0195] (With respect to any figure, description, or example in this specification, such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the first WTRU and the second WTRU are UEs in the sidelink of a wireless communication system.

[0196] (With respect to any figure, description, or example in this specification, such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, in the uplink of a wireless communication system, the first WTRU is a UE and the second WTRU is a base station device.

[0197] (With respect to any figure, description, or example in this specification, such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the set of second WTRUs are a plurality of transmit-receive points in the uplink of a multi-TRP wireless communication system.

[0198] FIG. 13 illustrates an exemplary procedure for receiving a CP-OFDM signal based on phase noise cyclic division. In this example, the first WTRU or the set of first WTRUs that receive the CP-OFDM symbol from the second WTRU or the set of second WTRUs may perform one or more of the following: At 1301, receiving the CP-OFDM symbol; at 1302, performing channel estimation, equalization, and / or common phase error compensation in the frequency domain of the received CP-OFDM; at 1303, obtaining / determining, via (for example, signaling indication), the subcarrier group size M, and the length L of the frequency domain cyclic prefix CP and / or the length L of the frequency domain cyclic suffix CS ; at 1304, the parameters (for example, M, L CP , and / or L CS) is determined to be greater than 0, and at 1305, if so, the phase noise ICI components estimated in each sub-carrier group are averaged and phase noise ICI compensation is performed; at 1304, if the parameter is not greater than 0, at 1306, phase noise ICI estimation and compensation are performed for the user's assignment; at 1307, the sub-carriers are demodulated and the residual phase noise ICI power is compared with a threshold; at 1308, if the residual phase noise ICI power is below the threshold, the process may return to the first 1301; at 1308, if the phase noise ICI power exceeds the threshold 1309, the phase noise characteristics (e.g., phase noise spectral width) are determined based on the residual phase noise ICI power exceeding the threshold (e.g., 1308); and / or, at 1310, a high phase noise indication is sent that includes information about the amount of phase noise expected or experienced in the communication link, such as phase noise capability information and / or phase noise spectral width; when 1310 is complete, the process may return to any one of the preceding steps such as 1301.

[0199] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, channel estimation may be performed by the first WTRU or a set of the first WTRUs using a demodulation reference signal (e.g., DM-RS) inserted in the frequency domain within the allocated bandwidth of the WTRU.

[0200] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, common phase error compensation may be performed by the first WTRU or a set of the first WTRUs using a phase tracking reference signal (e.g., PT-RS) inserted in the frequency domain within the allocated bandwidth of the WTRU.

[0201] (For example, with respect to any figure, description, or example in this specification, such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the sub - carrier group size and the length of the frequency - domain cyclic prefix and / or the length of the frequency - domain cyclic suffix can be obtained by a first WTRU or a set of first WTRUs through upper - layer signaling, for example, via RRC phase noise configuration information.

[0202] (For example, with respect to any figure, description, or example in this specification, such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the sub - carrier group size and the length of the frequency - domain cyclic prefix and / or the length of the frequency - domain cyclic suffix can be obtained from signaling instructions transmitted by a second WTRU or a set of second WTRUs, for example, via the downlink shared control or data channel, PDCCH or PDSCH, or through MAC CE.

[0203] (For example, with respect to any figure, description, or example in this specification, such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the signaling instructions can be obtained through upper - layer signaling or can be transmitted by a second WTRU or a set of second WTRUs in a periodic, semi - periodic, on - demand, or event - based manner using the periodicity received in the phase noise configuration message, for example, via the downlink shared control or data channel, PDCCH or PDSCH, or MAC CE.

[0204] (For example, with respect to any figure, description, or example in this specification, such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the sub-carrier group size and the length of the frequency domain cyclic prefix and / or the length of the frequency domain cyclic suffix may be obtained by an index to a codebook of a predefined combination of the length of the frequency domain cyclic prefix and the length of the frequency domain cyclic suffix and the sub-carrier group size, which must be known to the first WTRU or the set of first WTRUs and the second WTRU or the set of second WTRUs for unambiguous detection.

[0205] (For example, with respect to any figure, description, or example in this specification, such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the sub-carrier group size and the length of the frequency domain cyclic prefix and / or the length of the frequency domain cyclic suffix may be obtained by the first WTRU or the set of first WTRUs through blind detection.

[0206] (For example, with respect to any figure, description, or example in this specification, such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the estimation of the phase noise ICI component may involve the first WTRU or the set of first WTRUs obtaining a set of ICI coefficients in each of one or more sub-carrier groups and further averaging the phase noise ICI components across the sub-carrier groups to benefit from frequency diversity.

[0207] (For example, with respect to any figure, description, or example in this specification, such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, performing phase noise ICI compensation may be based on applying the Hermitian conjugate of the phase noise ICI spectral response based on the phase noise ICI components averaged across the sub-carrier groups.

[0208] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the residual phase noise ICI power can be measured by the first WTRU or a set of first WTRUs from the average constellation error of the demodulated subcarrier complex symbols.

[0209] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the phase noise spectral width is measured by the first WTRU or a set of first WTRUs on the received symbol or set of symbols and can be expressed in units of Hz or the number of subcarriers for the current numerology.

[0210] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the threshold represents the maximum allowable phase noise ICI power, and when it is exceeded, the first WTRU or a set of first WTRUs sends a high phase noise indication requiring phase noise reduction to the second WTRU or a set of second WTRUs.

[0211] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the value of the threshold can be obtained by upper layer signaling, for example, via RRC phase noise configuration information.

[0212] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the value of the threshold can be sent by the second WTRU or a set of second WTRUs in a phase noise configuration message, for example, in a downlink shared control or data channel, PDCCH or PDSCH, or using MAC CE.

[0213] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the high phase noise indication may be reported by a first WTRU in an uplink shared control or data channel (e.g., PUCCH or PUSCH), or using MAC CE.

[0214] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the phase noise information may include phase noise capability information or the amount of phase noise experienced in a communication link.

[0215] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the phase noise information may include an indication of a preferred subcarrier partition to a second WTRU or set of second WTRUs, including a codebook of empirically defined combinations of the length of the frequency domain cyclic prefix and the length of the frequency domain cyclic suffix, and the subcarrier group size, known to the first WTRU or set of first WTRUs and the second WTRU or set of second WTRUs.

[0216] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the phase noise capability may include an indication of a priori known radio frequency category or oscillator quality class within a set of a priori categories or classes, or an indication of the expected amount of phase noise experienced under typical operating conditions such as temperature, power, or cell load.

[0217] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise in the phase noise capability may be represented as a phase noise spectral width measured in Hz or number of subcarriers for a given numerology or set of numerologies.

[0218] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise can be expressed as the number of non-negligible ICI coefficients in the phase noise spectrum response under current operating conditions.

[0219] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise can be expressed as the power of the experienced phase noise impairment in watts, milliwatts, dBW, dBm, or any other suitable unit.

[0220] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise can be expressed as an indication of the post-detection signal-to-noise ratio measured at the receiving entity after equalization and phase noise compensation.

[0221] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise can be expressed as the residual mean squared error of detection at the output of the phase noise compensation algorithm.

[0222] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the amount of phase noise can be expressed as the magnitude of the error vector of the constellation seen at the receiving entity after equalization.

[0223] (For example, with respect to any figure, description, or example in this specification such as FIGS. 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, in the downlink of a wireless communication system, the first WTRU is a UE and the second WTRU is a base station device.

[0224] (For example, with respect to any figure, description, or example in this specification, such as Figures 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the second set of WTRUs are a plurality of transmission and reception points in the downlink of a multi-TRP wireless communication system.

[0225] (For example, with respect to any figure, description, or example in this specification, such as Figures 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the first WTRU and the second WTRU are UEs in the sidelink of a wireless communication system.

[0226] (For example, with respect to any figure, description, or example in this specification, such as Figures 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, in the uplink of a wireless communication system, the first WTRU is a base station device and the second WTRU is a UE.

[0227] (For example, with respect to any figure, description, or example in this specification, such as Figures 11, 12, 13, etc.) In one example of the transmission procedure described in this specification, the first set of WTRUs are a plurality of transmission and reception points in the uplink of a multi-TRP wireless communication system.

[0228] Figure 14 illustrates an exemplary method for determining and indicating high phase noise by one or more techniques described herein. In this example, the method may be implemented by any device disclosed herein (e.g., a network node, a WTRU, a TRP, a base station, etc.). At 1401, the device may receive a configuration message, which may include a subcarrier group size, a length of a frequency domain cyclic prefix (FD-CP), and / or a length of a frequency domain cyclic suffix (FD-CS). At 1402, the device may process received symbols based on the configuration information. This processing may include receiving a CP-OFDM symbol for a communication link based on an average phase noise estimated from one or more subcarrier groups using phase noise inter carrier interference (ICI) compensation of the CP-OFDM symbol after removal of any one or more of the FP-CP or FD-CS, based on the subcarrier group size. The processing may also include demodulating the subcarriers of one or more subcarrier groups and comparing the residual phase noise ICI power of the demodulated subcarriers to a threshold. At 1403, the device may determine phase noise characteristics based on the residual phase noise ICI power exceeding the threshold. At 1404, the device may send a high phase noise indication including the phase noise characteristics, where the phase noise characteristics include information regarding an expected amount or a measured amount of phase noise in a communication link for receiving a CP-OFDM symbol. In one example that may be combined with other cases and examples, the configuration message is part of a control channel transmission, a MAC CE, or an RRC signaling. In one example that may be combined with other cases and examples, the configuration message is determined through blind decoding. In one example that may be combined with other cases and examples, the threshold is determined from RRC signaling. In one example that may be combined with other cases and examples, the high phase noise indication is part of an uplink control channel message, an uplink shared channel message, or a MAC CE.In one example that can be combined with other examples and embodiments, the phase noise characteristic includes the phase noise spectral width. In one example that can be combined with other examples and embodiments, the device is a wireless transceiver unit or a base station. As described herein, a transmitting entity and / or a receiving entity can generally refer to any device described herein, such as a WTRU and / or a base station.

[0229] As described herein, the upper layer may refer to one or more layers in the protocol stack, or a particular sublayer within the protocol stack. This protocol stack may be composed of one or more layers within a WTRU or network node (e.g., eNB, gNB, other functional entities, etc.), where each layer may have one or more sublayers. Each layer / sublayer may perform one or more functions. Each layer / sublayer can communicate directly or indirectly with one or more of the other layers / sublayers. In some cases, these layers may be numbered, such as layer 1, layer 2, and layer 3. For example, layer 3 may be composed of one or more of the following. That is, they may be the non-access stratum (NAS), Internet protocol (IP), and / or radio resource control (RRC). For example, layer 2 may be composed of one or more of the following. That is, they may be packet data convergence control (PDCP), radio link control (RLC), and / or medium access control (MAC). For example, layer 3 may be composed of physical (PHY) layer type operations. The higher the layer number, the more upper the layer is relative to other layers (e.g., layer 3 is more upper than layer 1). In some cases, the foregoing examples may be referred to as the layer / sublayer itself, regardless of the number of layers, and may be referred to as the upper layer as described herein. For example, the upper layer may refer to one or more of the following layers / sublayers from the topmost to the bottommost, i.e., the NAS layer, the RRC layer, the PDCP layer, the RLC layer, the MAC layer, and / or the PHY layer. Any reference in this specification to the upper layer in relation to a process, device, or system will refer to a layer that is more upper than the layer of the process, device, or system. In some cases, a reference to the upper layer in this specification may refer to a function or operation performed by one or more of the layers described herein.In some cases, references to upper layers in this specification may refer to information sent or received by one or more of the layers described in this specification. In some cases, references to upper layers in this specification may refer to configurations sent and / or received by one or more of the layers described in this specification.

[0230] Features and elements are described above in specific combinations (e.g., embodiments, methods, examples, etc.), but those skilled in the art will understand that each feature or element can be used alone or in any combination with other features and elements. For example, as disclosed herein, there may be methods described in connection with figures for illustrative purposes, and those skilled in the art will understand that one or more features or elements from such methods can be used alone or in combination with one or more features from other methods described elsewhere. Additionally, any method described herein can be implemented in a device that executes a computer program, software, and / or firmware incorporated in a computer-readable medium for execution by a computer and / or processor operably connected to a transceiver of the device (e.g., wireless or wired). Examples of computer-readable media include electronic signals (transmitted via wired or wireless connections) and computer-readable storage media. Examples of computer-readable storage media include, but are not limited to, magnetic media such as read-only memory (ROM), random access memory (RAM), registers, cache memory, semiconductor memory devices, internal hard disks, and removable disks, magneto-optical media, and optical media such as CD-ROM disks and digital versatile disks (DVDs). A processor associated with software can be used to implement a radio frequency transceiver for use in a WTRU, UE, terminal, base station, RNC, or any host computer.

Claims

1. A method implemented by a device, Receiving a configuration message, wherein the configuration message includes the subcarrier group size, the length of the frequency domain cyclic prefix (FD-CP), or the length of the frequency domain cyclic suffix (FD-CS). Performing phase noise inter-carrier interference (ICI) compensation for CP-OFDM symbols based on the configuration message, wherein the configuration message is part of control channel transmission, MAC CE, or RRC signaling, Demodulating subcarriers from one or more subcarrier groups, and comparing the residual phase noise ICI power of the demodulated subcarriers with a threshold, The phase noise characteristics are determined based on the residual phase noise ICI power that exceeds the threshold, Sending a high-phase-noise instruction that includes the aforementioned phase-noise characteristics, wherein the high-phase-noise instruction is part of an uplink control channel message, an uplink shared channel message, or a MAC CE. Methods implemented by devices, including those mentioned above.

2. The method according to claim 1, wherein the phase noise ICI compensation of the CP-OFDM symbol is performed using the mean phase noise estimated from one or more subcarrier groups, further based on the communication link for receiving the CP-OFDM symbol, the mean phase noise is based on the size of the subcarrier group after the removal of one or more FP-CP or FD-CS.

3. The method according to claim 1, wherein the configuration message is determined through blind decoding.

4. The method according to claim 1, wherein the threshold is determined from RRC signaling.

5. The method according to claim 1, wherein the phase noise characteristics include information regarding the expected amount of phase noise or the measured amount of phase noise in the communication link for receiving the CP-OFDM symbol.

6. The method according to claim 1, wherein the phase noise characteristics include the phase noise spectral width.

7. The method according to claim 1, wherein the device is a wireless transmit / receive unit or a base station.

8. It is a device, A processor operably connected to the transceiver, Equipped with, The processor and the transceiver are configured to receive a configuration message, the configuration message includes the subcarrier group size, the length of the frequency domain cyclic prefix (FD-CP), or the length of the frequency domain cyclic suffix (FD-CS), The processor is configured to perform phase noise inter-carrier interference (ICI) compensation for CP-OFDM symbols based on the configuration message, and the configuration message is part of control channel transmission, MAC CE, or RRC signaling. The processor is configured to demodulate subcarriers of one or more subcarrier groups and to compare the residual phase noise ICI power of the demodulated subcarriers with a threshold value. The processor is configured to determine the phase noise characteristics based on the residual phase noise ICI power that exceeds the threshold, The processor and the transceiver are configured to send a high-phase-noise instruction including the phase-noise characteristics, and the high-phase-noise instruction is part of an uplink control channel message, an uplink shared channel message, or a MAC CE. device.

9. The device according to claim 8, wherein the phase noise ICI compensation of the CP-OFDM symbol is performed using the mean phase noise estimated from one or more subcarrier groups, further based on a communication link for receiving the CP-OFDM symbol, the mean phase noise being based on the size of the subcarrier group after the removal of one or more FP-CP or FD-CS.

10. The device according to claim 8, wherein the configuration message is determined through blind decoding.

11. The device according to claim 8, wherein the threshold is determined from RRC signaling.

12. The device according to claim 8, wherein the phase noise characteristics include information regarding the expected amount of phase noise or the measured amount of phase noise in the communication link for receiving the CP-OFDM symbol.

13. The device according to claim 8, wherein the phase noise characteristics include the phase noise spectral width.

14. The device according to claim 8, wherein the device is a wireless transmit / receive unit or a base station.

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