FILTER DEVICE, ANTENNA DEVICE, AND ANTENNA MODULE

Abstract

A filter device (100) comprises: an LC-series resonator (RC1) for series resonance at a series resonance frequency (F1) by an inductor (L1) and a capacitor (C1); and an LC-series resonator (RC2) for series resonance at a series resonance frequency (F2) by an inductor (L2) and a capacitor (C2). In the filter device (100), the LC-series resonator (RC1) and the LC-series resonator (RC2) are connected in parallel, and are in parallel resonance at a parallel resonance frequency (F3). The series resonance frequency (F2) is lower than the series resonance frequency (F1), and the parallel resonance frequency (F3) is between the series resonance frequency (F1) and the series resonance frequency (F2).

Description

[Technical field]

[0001] The present disclosure relates to a filter device, an antenna device, and an antenna module, and more particularly to a technique for reducing signal loss. [Background technology]

[0002] High-frequency circuits are provided with filter devices such as band-stop filters and band-pass filters. One example of a filter device provided in a high-frequency circuit is the filter device disclosed in Japanese Patent No. 6531824 (Patent Document 1). The filter device disclosed in Patent Document 1 includes a first inductor and a first capacitor that form a first series circuit, and a second inductor that is connected in parallel to the first series circuit. [Prior art documents] [Patent documents]

[0003] [Patent Document 1] Patent No. 6531824 Summary of the Invention [Problem to be solved by the invention]

[0004] In the filter device of Patent Document 1, at frequencies lower than the attenuation band of the parallel resonance, the reactance characteristic is increased compared to when the second inductor is used alone, which causes signal loss due to impedance deviation in the filter device of Patent Document 1.

[0005] The present disclosure has been made to solve such problems, and its purpose is to reduce signal loss in a frequency band lower than the attenuation band of parallel resonance in a filter device for high-frequency signals. [Means for solving the problem]

[0006] A filter device according to the present disclosure includes a first series resonator that resonates in series at a first resonant frequency by a first inductor and a first capacitor connected in series with the first inductor, and a second series resonator that resonates in series at a second resonant frequency by a second inductor and a second capacitor connected in series with the second inductor. The first and second series resonators are connected in parallel and resonate in parallel at a third resonant frequency, the second resonant frequency being lower than the first resonant frequency and the third resonant frequency being between the first resonant frequency and the second resonant frequency. Effect of the Invention

[0007] The filter device according to the present disclosure includes a first series resonator that resonates in series at a first resonant frequency by a first inductor and a first capacitor, and a second series resonator that resonates in series at a second resonant frequency by a second inductor and a second capacitor, the first series resonator and the second series resonator being connected in parallel to resonate in parallel at a third resonant frequency in a third frequency band. With this configuration, it is possible to reduce signal loss in a frequency band lower than the attenuation band of the parallel resonance. [Brief description of the drawings]

[0008] [Figure 1] 1 is a diagram illustrating a configuration of an antenna device according to a first embodiment. [Diagram 2] 4 is a diagram illustrating an example of reactance characteristics of the filter device according to the first embodiment. FIG. [Diagram 3] 5 is a diagram illustrating an example of an insertion loss of the filter device according to the first embodiment. FIG. [Figure 4] 11A and 11B are a circuit diagram and an equivalent circuit diagram of a filter device according to a second embodiment. [Diagram 5] 11 is a diagram illustrating an example of reactance characteristics of the filter device according to the second embodiment. FIG. [Figure 6] 11 is a diagram illustrating an example of an insertion loss of the filter device according to the second embodiment. [Figure 7] FIG. 7 is a vertical enlarged view of the area shown in FIG. 6. [Figure 8] 11 is a diagram illustrating an example of reactance characteristics of the filter device according to the second embodiment. FIG. [Figure 9] 11 is a diagram illustrating an example of an insertion loss of the filter device according to the second embodiment. [Figure 10] FIG. 10 is a vertical enlarged view of the area shown in FIG. [Figure 11] FIG. 13 is a diagram illustrating an example of reactance characteristics of a filter device according to a first modification of the second embodiment. [Figure 12] 13 is a diagram showing an example of an insertion loss of a filter device according to a first modification of the second embodiment. FIG. [Figure 13] FIG. 13 is a vertical enlarged view of the area shown in FIG. [Figure 14] FIG. 13 is a circuit diagram of a filter device according to a second modification of the second embodiment. [Figure 15] FIG. 13 is a diagram illustrating an example of reactance characteristics of a filter device according to a second modification of the second embodiment. [Figure 16] 13 is a diagram showing an example of an insertion loss of a filter device according to a second modification of the second embodiment. FIG. [Figure 17] FIG. 17 is a vertical enlarged view of the area shown in FIG. 16. [Figure 18] 13A and 13B are diagrams illustrating the configuration of an antenna device according to another modified example. [Figure 19] 13 is a diagram showing a configuration of an antenna module according to a third embodiment. FIG. [Figure 20] 13 is an external view of an antenna module according to a third embodiment. FIG. [Figure 21] FIG. 11 is a circuit diagram of a filter device according to a fourth embodiment. [Figure 22] 11A and 11B are diagrams illustrating an example of changes in reactance characteristics before and after an inductor is added. [Figure 23] FIG. 13 is a diagram showing an example of a change in insertion loss before and after an inductor is added. [Figure 24] 11A and 11B are diagrams illustrating an example of changes in reactance characteristics before and after an inductor is added. [Diagram 25]FIG. 13 is a diagram showing an example of a change in insertion loss before and after an inductor is added. [Figure 26] FIG. 13 is a circuit diagram of a filter device according to a fifth embodiment. [Figure 27] FIG. 11 is a diagram showing an example of a change in reactance characteristics before and after adding a capacitor. [Figure 28] FIG. 13 is a diagram showing an example of a change in insertion loss before and after adding a capacitor. [Figure 29] FIG. 11 is a diagram showing an example of a change in reactance characteristics before and after adding a capacitor. [Diagram 30] FIG. 13 is a diagram showing an example of a change in insertion loss before and after adding a capacitor. DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

[0009] Hereinafter, embodiments of the present disclosure will be described in detail with reference to the drawings. In the drawings, the same or corresponding parts are designated by the same reference characters and their description will not be repeated.

[0010] [Embodiment 1] <Basic configuration of antenna device> 1 is a diagram showing a configuration of an antenna device 1000 according to the first embodiment. The antenna device 1000 includes a feeding circuit RF1, a filter device 100, and an antenna 155. The antenna device 1000 is mounted on a communication device such as a mobile terminal such as a mobile phone, a smartphone, or a tablet, or a personal computer with a communication function.

[0011] The power supply circuit RF1 supplies a high-frequency signal in the f1 band frequency band and a high-frequency signal in the f2 band frequency band to the antenna 155. The antenna 155 can radiate the high-frequency signal in the f1 band and the high-frequency signal in the f2 band supplied from the power supply circuit RF1 into the air as radio waves. The f1 band frequency band is, for example, the 5 GHz band (5.15-5.7 GHz) of Wi-Fi (registered trademark). The f2 band frequency band is, for example, the 2.4 GHz band (2.4-2.5 GHz) of Wi-Fi (registered trademark). The antenna 155 is, for example, a monopole antenna.

[0012] The filter device 100 is a trap filter that prevents the passage of a high-frequency signal in a specific frequency band and attenuates the signal. The filter device 100 is also called a band elimination filter. The filter device 100 in the first embodiment is configured to attenuate a high-frequency signal in the f3 frequency band. The f3 frequency band includes, for example, n77 (3.3-4.2 GHz) and n78 (3.3-3.8 GHz) of 5G-NR (New Radio).

[0013] The f1 band to the f3 band are adjacent frequency bands. Whether or not the frequency bands are adjacent can be determined using a bandwidth and a center frequency for that bandwidth. For example, if the ratio of the bandwidth between the frequency end of the f1 band and the frequency end of the f2 band and the center frequency for that bandwidth is within a predetermined range, the f1 band and the f2 band are determined to be adjacent. Note that whether or not the frequency bands are adjacent may be determined by other methods. In the filter device 100, the f1 band and the f2 band are pass bands, and the f3 band is an attenuation band.

[0014] 1 has a terminal P1 and a terminal P2. The terminal P1 is a terminal for connecting the filter device 100 to a transmission line on the feed circuit RF1 side. The terminal P2 is a terminal for connecting the filter device 100 to a transmission line on the antenna 155 side.

[0015] When the power feed circuit RF1 supplies a high-frequency signal to the antenna 155 via the filter device 100, the terminal P1 serves as an input terminal and the terminal P2 serves as an output terminal. When a high-frequency signal received by the antenna 155 is transmitted to a circuit on the power feed circuit RF1 side via the filter device 100, the terminal P1 serves as an output terminal and the terminal P2 serves as an input terminal. The filter device 100 does not have a ground electrode, and there is no need to consider the influence of the wiring pattern, which makes it easy to implement in each device.

[0016] 1, the filter device 100 includes an inductor L1, a capacitor C1, an inductor L2, and a capacitor C2. The LC series resonator RC1 is formed by connecting the inductor L1 and the capacitor C1 in series. The LC series resonator RC2 is formed by connecting the inductor L2 and the capacitor C2 in series.

[0017] The LC series resonators RC1 and RC2 are connected in parallel. The LC parallel resonator RC3 is an LC parallel resonator formed by connecting the LC series resonators RC1 and RC2 in parallel. The LC series resonators RC1, RC2, and RC3 are disposed between the terminal P1 and the terminal P2.

[0018] Fig. 2 is a diagram showing an example of the reactance characteristic of filter device 100 according to the first embodiment. In Fig. 2, the horizontal axis represents frequency, and the vertical axis represents reactance. Fig. 3 is a diagram showing an example of the insertion loss of filter device 100 according to the first embodiment. In Fig. 3, the horizontal axis represents frequency, and the vertical axis represents insertion loss.

[0019] 2, the reactance characteristics of the filter device 100 of the first embodiment are indicated by line Ln1, and the reactance characteristics of a comparative filter device are indicated by line Ln2. Although not shown, the comparative filter device has a configuration in which an inductor L2 is connected in parallel to an LC series resonator formed of an inductor L1 and a capacitor C1.

[0020] Specifically, the filter device 100 was simulated with an inductor L1 of 1.4 nH, an inductor L2 of 3.98 nH, a capacitor C1 of 0.6 pF, and a capacitor C2 of 1.1 pF. The comparative filter device was simulated with an inductor L1 of 2.6 nH, an inductor L2 of 3.98 nH, and a capacitor C1 of 0.32 pF.

[0021] 2, the comparative filter device has a series resonance frequency F1 of 5.5 GHz in the pass band (f1 band) and a parallel resonance frequency F3 of 3.5 GHz in the attenuation band (f3 band). However, the comparative filter device cannot make the reactance zero at frequencies lower than the parallel resonance frequency F3.

[0022] In contrast, in the filter device 100, as shown by the line Ln1, the series resonance frequency F1 in the pass band (f1 band) is 5.5 GHz, the series resonance frequency F2 in the pass band (f2 band) is 2.4 GHz, and the parallel resonance frequency F3 in the attenuation band (f3 band) is 3.5 GHz. In this way, in the filter device 100, the reactance can be set to 0 at the frequency F2 lower than the parallel resonance frequency F3.

[0023] In Fig. 3, the insertion loss of the filter device 100 of the first embodiment is indicated by line Ln3, and the insertion loss of the comparative filter device is indicated by line Ln4. As shown in Fig. 3, it can be seen that the insertion loss at frequency F2 decreases from the value at point a in the comparative filter device to the value at point b in the filter device 100. In this way, in the filter device 100, the signal loss can be reduced at frequency F2 which is lower than the parallel resonance frequency F3.

[0024] The filter device 100 is provided in an antenna device 1000 capable of radiating signals having a series resonant frequency F1 and a series resonant frequency F2 as resonant frequencies, so that the antenna device 1000 can appropriately transmit and receive signals in a pass band (f1 band) and a pass band (f2 band).

[0025] [Embodiment 2] <Basic configuration of filter device> 4 is a circuit diagram and an equivalent circuit diagram of a filter device 110 according to the second embodiment. As shown in the circuit diagram of FIG. 4(A), the filter device 110 according to the second embodiment has the same configuration as the filter device 100 according to the first embodiment, except that the inductor L1 and the inductor L2 are magnetically coupled to each other. In the filter device 110, a mutual inductance M occurs between the inductor L1 and the inductor L2. The filter device 110 is a circuit with additive polarity in which the winding directions of the coils constituting the inductor L1 and the inductor L2 are opposite to each other.

[0026] The equivalent circuit diagram shown in Fig. 4(B) shows an equivalent circuit diagram of the circuit of the filter device 110 shown in Fig. 4(A). In Fig. 4(B), mutual inductance +M and mutual inductance -M are shown on the paths.

[0027] Fig. 5 is a diagram showing an example of the reactance characteristics of filter device 110 according to the second embodiment. In Fig. 5, the horizontal axis represents frequency, and the vertical axis represents reactance. Fig. 6 is a diagram showing an example of the insertion loss of filter device 110 according to the second embodiment. In Fig. 6, the horizontal axis represents frequency, and the vertical axis represents insertion loss. Fig. 7 is a vertical enlarged view of region Rg1 shown in Fig. 6.

[0028] 5, the reactance characteristics of the filter device 100 without magnetic coupling according to the first embodiment are indicated by line Ln5, the reactance characteristics of the filter device 110 with magnetic coupling according to the second embodiment are indicated by line Ln6, and the reactance characteristics of a comparative filter device are indicated by line Ln7. In the filter device 110, mutual inductance M occurs due to magnetic coupling.

[0029] Specifically, the filter device 100 without magnetic coupling according to the first embodiment was simulated with inductor L1 set to 1.4 nH, inductor L2 set to 3.98 nH, capacitor C1 set to 0.6 pF, and capacitor C2 set to 1.1 pF. The filter device 110 with magnetic coupling according to the second embodiment was simulated with inductor L1 set to 3.1 nH, inductor L2 set to 1.0 nH, capacitor C1 set to 0.4 pF, capacitor C2 set to 3.8 pF, coupling coefficient k set to 0.5, and mutual inductance M set to 0.88 nH. The filter device for comparison was simulated with inductor L1 set to 2.6 nH, inductor L2 set to 3.98 nH, and capacitor C1 set to 0.32 pF.

[0030] 5, the comparative filter device has a series resonance frequency F1 in the pass band (f1 band) of 5.5 GHz and a parallel resonance frequency F3 in the attenuation band (f3 band) of 3.5 GHz. However, the comparative filter device cannot make the reactance zero at frequencies lower than the parallel resonance frequency F3.

[0031] In contrast, in the filter device 100 and the filter device 110, as shown by lines Ln5 and Ln6, the series resonance frequency F1 in the pass band (f1 band) is 5.5 GHz, the series resonance frequency F2 in the pass band (f2 band) is 2.4 GHz, and the parallel resonance frequency F3 in the attenuation band (f3 band) is 3.5 GHz. In this way, in the filter device 100 and the filter device 110, the reactance can be set to 0 at the frequency F2 lower than the parallel resonance frequency F3.

[0032] In Fig. 6, the insertion loss of the filter device 100 of the first embodiment is indicated by line Ln8, the insertion loss of the filter device 110 of the second embodiment is indicated by line Ln9, and the insertion loss of the comparative filter device is indicated by line Ln10. As shown in Fig. 6, the filter device 100 and the filter device 110 have a series resonance frequency F2, and therefore can suppress the insertion loss near the series resonance frequency F2 compared to the comparative filter device. In other words, the filter device 100 and the filter device 110 can realize a narrow-band filter device in which the attenuation characteristics change sharply near the parallel resonance frequency F3 compared to the comparative filter device.

[0033] FIG. 7 shows a waveform in which the vertical axis (insertion loss) direction of the region Rg1 shown in FIG. 6 is enlarged. 7 The ratio of the horizontal axis (frequency) direction in Fig. 6 , only the ratio in the vertical axis (insertion loss) direction is enlarged.

[0034] 7, the line Ln9 of the filter device 110 has attenuation characteristics that change more steeply in the vicinity of the parallel resonance frequency F3 than the line Ln8 of the filter device 100. In this way, due to the occurrence of mutual inductance M, the filter device 110 can reduce signal loss in a wide band d2 around the pass band (f1 band) of the series resonance frequency F1 more than the filter device 100 without magnetic coupling, and can also reduce signal loss in a wide band d1 around the pass band (f2 band) of the series resonance frequency F2.

[0035] Next, a comparison is made again for combinations of L and C values ​​that provide the same insertion loss at parallel resonance frequency F3. Figures 8 to 10 are diagrams in which the value of inductor L1 is reduced so that the reactance and insertion loss in the attenuation band of filter device 100 without magnetic coupling are at the same levels as those of filter device 110 with magnetic coupling, as compared with Figures 5 to 7 above.

[0036] Fig. 8 is a diagram showing an example of the reactance characteristics of filter device 110 according to the second embodiment. In Fig. 8, the horizontal axis represents frequency, and the vertical axis represents reactance. Fig. 9 is a diagram showing an example of the insertion loss of filter device 110 according to the second embodiment. In Fig. 9, the horizontal axis represents frequency, and the vertical axis represents insertion loss. Fig. 10 is a vertical axis enlarged view of region Rg2 shown in Fig. 9.

[0037] In FIG. 8, the reactance characteristics of the filter device 100 without magnetic coupling are indicated by a line Ln11, and the reactance characteristics of the filter device 110 with magnetic coupling according to the second embodiment are indicated by a line Ln12.

[0038] Specifically, the filter device 100 was simulated with an inductor L1 of 0.8 nH, an inductor L2 of 2.3 nH, a capacitor C1 of 1.1 pF, and a capacitor C2 of 1.8 pF. The filter device 110 was simulated with an inductor L1 of 3.1 nH, an inductor L2 of 1.0 nH, a capacitor C1 of 0.4 pF, a capacitor C2 of 3.8 pF, a coupling coefficient k of 0.5, and a mutual inductance M of 0.88 nH.

[0039] As shown by lines Ln11 and Ln12 in FIG. 8, the filter device 100 and the filter device 110 have a series resonance frequency F1 in the pass band (f1 band) of 5.5 GHz, a series resonance frequency F2 in the pass band (f2 band) of 2.4 GHz, and a parallel resonance frequency F3 in the attenuation band (f3 band) of 3.5 GHz.

[0040] 9, the insertion loss of filter device 100 is indicated by line Ln13, and the insertion loss of filter device 110 of the second embodiment is indicated by line Ln14. As shown in Fig. 9, filter device 100 and filter device 110 have the same level of reactance at parallel resonance frequency F3, as shown by point c.

[0041] Fig. 10 shows a waveform in which the vertical axis (insertion loss) direction of region Rg2 shown in Fig. 9 is expanded. To make it easier to see the difference between lines Ln13 and Ln14, the ratio in the horizontal axis (frequency) direction in Fig. 10 is the same as in Fig. 9, and only the ratio in the vertical axis (insertion loss) direction is expanded.

[0042] 10, the line Ln14 of the filter device 110 has attenuation characteristics that change more steeply in the vicinity of the parallel resonance frequency F3 than the line Ln13 of the filter device 100. As a result, even when the insertion loss is at the same level, the filter device 110 can reduce signal loss in a wide band d2 around the pass band (f1 band) of the series resonance frequency F1 more than the filter device 100 by magnetic coupling, and can reduce signal loss in a wide band d1 around the pass band (f2 band) of the series resonance frequency F2.

[0043] [Modification 1 of the second embodiment] In the first modification of the second embodiment, a case will be described in which, compared to the second embodiment, it is not necessary to set the pass band (f1 band) of the series resonant frequency F1 in a frequency band close to the parallel resonant frequency F3.

[0044] FIG. 11 is a diagram showing an example of the reactance characteristics of the filter device according to the first modification of the second embodiment. In FIG. 11, the horizontal axis represents frequency, and the vertical axis represents reactance. FIG. 12 is a diagram showing an example of the insertion loss of the filter device according to the first modification of the second embodiment. In FIG. 12, the horizontal axis represents frequency, and the vertical axis represents insertion loss. FIG. 13 is a vertical enlarged view of region Rg3 shown in FIG. 12. Here, FIGS. 11 to 13 are diagrams in which the pass band (f1 band) of series resonant frequency F1 is set to an extremely high frequency by making inductor L1 smaller, as compared with the above-mentioned FIGS. 5 to 7.

[0045] In FIG. 11, the reactance characteristics of the filter device 110 according to the second embodiment are indicated by a line Ln15, and the reactance characteristics of the filter device according to the first modification of the second embodiment are indicated by a line Ln16.

[0046] Specifically, the filter device 110 was simulated with an inductor L1 of 3.1 nH, an inductor L2 of 1.0 nH, a capacitor C1 of 0.4 pF, a capacitor C2 of 3.8 pF, and a coupling coefficient k of 0.5. The filter device of Modification 1 was simulated with an inductor L1 of 0.01 nH, an inductor L2 of 1.0 nH, a capacitor C1 of 4.6 pF, a capacitor C2 of 3.8 pF, and a coupling coefficient k of 0.0.

[0047] 11, in the filter device of Modification 1, the series resonant frequency F1 of the pass band (f1 band) is 23.5 GHz, the series resonant frequency F2 of the pass band (f2 band) is 2.4 GHz, and the parallel resonant frequency F3 of the attenuation band (f3 band) is 3.5 GHz. In this way, when it is not necessary to set the pass band near the high side of the attenuation band (f3 band), it is possible to change only the frequency of the series resonant frequency F1 while keeping the series resonant frequency F2 and the parallel resonant frequency F3 the same by reducing the inductor value.

[0048] 12, the insertion loss of the filter device 110 is indicated by a line Ln17, and the insertion loss of the filter device of Modification 1 is indicated by a line Ln18. In the filter device of Modification 1 shown in FIG 12, the series resonance frequency F1 is set to an extremely high frequency.

[0049] Fig. 13 shows a waveform in which the vertical axis (insertion loss) direction of region Rg3 shown in Fig. 12 is expanded. To make it easier to see the difference between lines Ln17 and Ln18, the ratio in the horizontal axis (frequency) direction in Fig. 13 is the same as in Fig. 12, and only the ratio in the vertical axis (insertion loss) direction is expanded.

[0050] 13, the line Ln18 of the filter device of the first modification has less signal loss in a wide band d1 around the pass band (f2 band) of the series resonance frequency F2, which is on the lower side with respect to the parallel resonance frequency F3, than the line Ln17 of the filter device 110. In this way, according to the filter device of the first modification, when it is not necessary to set the pass band near the higher side of the attenuation band (f3 band), it is possible to reduce signal loss on the other side (for example, the lower side).

[0051] [Modification 2 of the second embodiment] <Basic configuration of filter device> Fig. 14 is a circuit diagram of a filter device 150 according to the second modification of the second embodiment. As shown in the circuit diagram of Fig. 14, in the filter device 150 according to the second modification of the second embodiment, an inductor L1 and an inductor L2 are magnetically coupled to each other, and a mutual inductance M is generated between the inductors L1 and L2. The filter device 150 is a depolarized circuit in which the coils constituting the inductors L1 and L2 are wound in the same direction.

[0052] Although not shown, an equivalent circuit diagram of the filter device 150 of the second modification is a diagram in which the mutual inductance +M shown on the path in FIG. 4B is changed to -M, and the mutual inductance -M is changed to +M.

[0053] Fig. 15 is a diagram showing an example of the reactance characteristics of filter device 150 in Modification 2 of Embodiment 2. In Fig. 15, the horizontal axis represents frequency, and the vertical axis represents reactance. Fig. 16 is a diagram showing an example of the insertion loss of filter device 150 in Modification 2 of Embodiment 2. In Fig. 16, the horizontal axis represents frequency, and the vertical axis represents insertion loss. Fig. 17 is a vertical enlarged view of region Rg5 shown in Fig. 16.

[0054] In FIG. 15, the reactance characteristic of the additive polarity filter device 110 of the second embodiment is indicated by a line Ln23, and the reactance characteristic of the deductive polarity filter device 150 of the second modification of the second embodiment is indicated by a line Ln24.

[0055] Specifically, the filter device 110 was simulated with an inductor L1 of 3.1 nH, an inductor L2 of 1.0 nH, a capacitor C1 of 0.4 pF, a capacitor C2 of 3.8 pF, and a coupling coefficient k of 0.5. The filter device 150 of the second modification was simulated with an inductor L1 of 3.1 nH, an inductor L2 of 0.4 nH, a capacitor C1 of 1.3 pF, a capacitor C2 of 2.9 pF, and a coupling coefficient k of 0.5.

[0056] 15, in the filter device 110 and the filter device 150 of the second modification, as shown by lines Ln23 and Ln24, the series resonance frequency F1 in the pass band (f1 band) is 5.5 GHz, the series resonance frequency F2 in the pass band (f2 band) is 2.4 GHz, and the parallel resonance frequency F3 in the attenuation band (f3 band) is 3.5 GHz. In this way, in the filter device 110 and the filter device 150 of the second modification, the reactance can be set to 0 at the frequency F2 lower than the parallel resonance frequency F3.

[0057] 16, the insertion loss of the filter device 110 is indicated by a line Ln25, and the insertion loss of the filter device 150 of Modification 2 is indicated by a line Ln26. As indicated by the arrow from point a to point b in Fig. 16, the additive polarity filter device 110 is a narrower-band filter device in which the attenuation characteristics change more steeply in the vicinity of the parallel resonance frequency F3 than the deductive polarity filter device 150 of Modification 2.

[0058] Fig. 17 shows a waveform in which the vertical axis (insertion loss) direction of region Rg5 shown in Fig. 16 is expanded. To make it easier to see the difference between lines Ln25 and Ln26, the ratio in the horizontal axis (frequency) direction in Fig. 17 is the same as in Fig. 16, and only the ratio in the vertical axis (insertion loss) direction is expanded.

[0059] 17, the line Ln25 of the additive polarity filter device 110 has attenuation characteristics that change more steeply in the band d1 near the parallel resonance frequency F3 than the line Ln26 of the deductive polarity filter device 150 of Modification 2. However, it can also be said that the filter device 150 of Modification 2 has a wider range of attenuation characteristics near the parallel resonance frequency F3 compared to the filter device 110.

[0060] As shown in FIG. 17, the line Ln26 of the depolarizing filter device 150 of the second modified example is in a band farther away from the parallel resonance frequency F3 (a band higher than F1 or a band lower than F2) than the line Ln25 of the additive polarizing filter device 110. low In this way, even filter devices with the same structure will have different characteristics depending on whether they are additive or deductive polarity. Circuit designers can design circuits with additive or deductive polarity, taking into account the desired characteristics.

[0061] [Other variations] 18 is a diagram showing the configuration of an antenna device 2000 according to another modification. The antenna device 2000 includes a feed circuit RF1, a filter device 200, and an antenna 155. The antenna device 2000 is different from the antenna device 1000 according to the first embodiment in the configuration of the filter device.

[0062] 18, the filter device 200 includes an inductor L1, a capacitor C1, an inductor L2, and a capacitor C2. The LC series resonator RC1 is an LC series resonator formed by connecting the inductor L1 and the capacitor C1 in series. The LC series resonator RC2 is an LC series resonator formed by connecting the capacitor C2 and the inductor L2 in series. Compared to the filter device 100, the filter device 200 has a structure in which the positions of the inductor L2 and the capacitor C2 are swapped. Note that the filter device 200 may have a structure in which the positions of the inductor L2 and the capacitor C1 are swapped.

[0063] [Embodiment 3] 19 is a diagram showing a configuration of an antenna module 4000 according to the third embodiment. The antenna module 4000 includes an antenna device 1000 and an antenna device 3000. The antenna device 3000 includes a feeding circuit RF2 and an antenna 165. The antenna module 4000 is mounted on a communication device such as a mobile terminal such as a mobile phone, a smartphone, or a tablet, or a personal computer equipped with a communication function.

[0064] The configuration of antenna device 1000 is the same as that of embodiment 1, and therefore description thereof will be omitted. A power feeding circuit RF2 of antenna device 3000 supplies a high-frequency signal in the f3 frequency band to antenna 165. Antenna 165 can radiate the high-frequency signal in the f3 band supplied from power feeding circuit RF2 into the air as a radio wave.

[0065] In the antenna device 1000, a high-frequency signal in the f3 band radiated from the antenna device 3000 provided in the same antenna module 4000 can become noise. Therefore, the filter device 100 is provided to remove the high-frequency signal in the f3 band that can become noise in the antenna device 1000 by increasing the insertion loss due to parallel resonance.

[0066] The antenna 155 and the antenna 165 are mounted on the same substrate 170. Although the antenna 155 and the antenna 165 are provided on the same substrate 170 in Fig. 19, they may be provided on different substrates as long as they are provided within the same antenna module 4000.

[0067] In the antenna module 4000, the filter device 100 of the antenna device 1000 can suppress the influence of the antenna device 3000. Therefore, in the antenna module 4000, the antenna device 1000 and the antenna device 3000 can be arranged close to each other. As a guide for the proximity, a case where the characteristics of the antenna device 1000 change due to the influence of the antenna device 3000 is shown.

[0068] FIG. 20 is an external view of an antenna module 4000 according to the third embodiment. As shown in FIG. 20, the antenna module 4000 includes an antenna device 1000 and an antenna device 3000. The antenna device 1000 includes an antenna 155 which is a monopole antenna, a filter device 100, and a feed circuit RF1. The antenna device 3000 includes an antenna 165 which is a monopole antenna, and a feed circuit RF2. The antennas 155 and 165 are not limited to monopole antennas, and may be an inverted-F antenna, a loop antenna, an array antenna, or the like. The antenna 155 is connected to the feed circuit RF1 via the filter device 100. The antenna 165 is connected to the feed circuit RF2.

[0069] The antenna module 4000 is capable of emitting radio waves in the f1, f2, and f3 bands. The antenna module 4000 includes an antenna device 1000 capable of emitting radio waves in the f1 and f2 bands, and an antenna device 3000 capable of emitting radio waves in the f3 band.

[0070] The above-mentioned filter device has been described as being designed taking into consideration only the inductor L1, the inductor L2, the capacitor C1, and the capacitor C2. However, in an actual filter device, it is necessary to design it taking into consideration stray capacitance, parasitic inductance, etc. It is also possible to use parasitic inductance as the inductor L1 or the inductor L2, to use the parasitic capacitance component of the inductor element itself as a capacitor, or to use the parasitic inductance component of the capacitor element as an inductor.

[0071] The above-described filter device may be provided with a matching circuit for matching impedance at the positions of terminals P1 and P2, and a switch for coupling and switching paths.

[0072] The above-mentioned filter device may be configured as an integrated part, which makes it possible to easily mount the filter device on each device without having to consider the influence of the wiring pattern.

[0073] [Embodiment 4] In the first embodiment, an LC parallel resonator has been described in which an LC series resonator RC1 formed by connecting an inductor L1 and a capacitor C1 in series and an LC series resonator RC2 formed by connecting an inductor L2 and a capacitor C2 in series are connected in parallel as shown in Fig. 1. In the second embodiment, a filter device 110 has been described in which the inductor L1 and the inductor L2 are magnetically coupled to each other in the filter device 100 of the first embodiment as shown in Fig. 4(A). In the fourth embodiment, a filter device 300 in which an inductor is provided in parallel with the filter device 110 of the second embodiment is described.

[0074] FIG. 21 is a circuit diagram of a filter device 300 according to the fourth embodiment. As shown in FIG. 21, the filter device 300 includes an inductor L1, an inductor L2, an inductor L3, a capacitor C1, and a capacitor C2. The inductors L1 and L2 are magnetically coupled to each other, but the inductor L3 (a third inductor) is not magnetically coupled to the inductors L1 and L2. The filter device before the inductor L3 is added corresponds to the filter device 110 according to the second embodiment. In the filter device 300 according to the fourth embodiment, the same components as those in the filter device 100 according to the first embodiment and the filter device 110 according to the second embodiment are denoted by the same reference numerals and will not be described in detail again. In the antenna device 1000 according to the first embodiment, the filter device 300 according to the fourth embodiment may be used instead of the filter device 100.

[0075] Fig. 22 is a diagram showing an example of change in reactance characteristics before and after adding inductor L3. In Fig. 22, the horizontal axis is frequency and the vertical axis is reactance. The graph in Fig. 22(a) is an example of reactance characteristics of the filter device 110 of the second embodiment before adding inductor L3. The graph in Fig. 22(b) is an example of reactance characteristics of the filter device 300 of the fourth embodiment after adding inductor L3.

[0076] Fig. 23 is a diagram showing an example of a change in insertion loss before and after adding inductor L3. In Fig. 23, the horizontal axis represents frequency, and the vertical axis represents insertion loss. The graph in Fig. 23(a) shows an example of the insertion loss of the filter device 110 of the second embodiment before adding inductor L3. The graph in Fig. 23(b) shows an example of the insertion loss of the filter device 300 of the fourth embodiment after adding inductor L3.

[0077] In Fig. 22, the reactance characteristic of the filter device 110 of the second embodiment is shown by a line Ln31, and the reactance characteristic of the filter device 300 of the fourth embodiment is shown by a line Ln32. In Fig. 23, the insertion loss of the filter device 110 of the second embodiment is shown by a line Ln33, and the insertion loss of the filter device 300 of the fourth embodiment is shown by a line Ln34. Specifically, the filter device 110 was simulated with an inductor L1 of 3.1 nH, an inductor L2 of 1.0 nH, a capacitor C1 of 0.4 pF, a capacitor C2 of 3.8 pF, and a coupling coefficient k of 0.5. The filter device 300 was simulated with an inductor L1 of 3.1 nH, an inductor L2 of 1.0 nH, an inductor L3 of 1.6 nH, a capacitor C1 of 0.4 pF, a capacitor C2 of 3.8 pF, and a coupling coefficient k of 0.5. That is, filter device 300 has the same values ​​as filter device 110, except for the value of inductor L3.

[0078] As shown in Fig. 22 and Fig. 23, the filter device 300 can add a new parallel resonant frequency F4 to the C-type region by connecting the inductor L3 in parallel. Here, the parallel resonant frequency F3 of the filter device 300 is shifted to F3' toward the higher frequency side of the graph compared to the filter device 110. In this way, adding the inductor L3 that is not magnetically coupled in parallel to the filter device 110 makes it possible to shift the parallel resonant frequency F3 toward the higher frequency side. On the other hand, in order to add a new parallel resonant frequency F4 while suppressing such a shift toward the higher frequency side, it is sufficient to adjust each numerical value. The adjustment of each numerical value will be described with reference to Figs. 24 and 25.

[0079] Fig. 24 is a diagram showing an example of change in reactance characteristics before and after adding inductor L3. In Fig. 24, the horizontal axis is frequency and the vertical axis is reactance. The graph in Fig. 24(a) shows an example of reactance characteristics of the filter device 110 of the second embodiment before adding inductor L3. The graph in Fig. 24(b) shows an example of reactance characteristics of the filter device 300 of the fourth embodiment after adding inductor L3.

[0080] Fig. 25 is a diagram showing an example of a change in insertion loss before and after adding inductor L3. In Fig. 25, the horizontal axis is frequency and the vertical axis is insertion loss. The graph in Fig. 25(a) shows an example of the insertion loss of the filter device 110 of the second embodiment before adding inductor L3. The graph in Fig. 25(b) shows an example of the insertion loss of the filter device 300 of the fourth embodiment after adding inductor L3.

[0081] In Fig. 24, the reactance characteristic of the filter device 110 of the second embodiment is shown by a line Ln31, and the reactance characteristic of the filter device 300 of the fourth embodiment is shown by a line Ln35. In Fig. 25, the insertion loss of the filter device 110 of the second embodiment is shown by a line Ln33, and the insertion loss of the filter device 300 of the fourth embodiment is shown by a line Ln36. Specifically, the filter device 110 was simulated with an inductor L1 of 3.1 nH, an inductor L2 of 1.0 nH, a capacitor C1 of 0.4 pF, a capacitor C2 of 3.8 pF, and a coupling coefficient k of 0.5. The filter device 300 was simulated with an inductor L1 of 1.4 nH, an inductor L2 of 1.0 nH, an inductor L3 of 1.5 nH, a capacitor C1 of 0.86 pF, a capacitor C2 of 3.8 pF, and a coupling coefficient k of 0.5. That is, the filter device 300 includes an inductor L1, an inductor L3, and a capacitor C 1 The value of is changed from that of the filter device 110.

[0082] 24 and 25, by adjusting each numerical value, the filter device 300 can make the series resonance frequency F1 in the pass band (f1 band), the series resonance frequency F2 in the pass band (f2 band), and the parallel resonance frequency F3 in the attenuation band (f3 band) similar to the frequencies of the filter device 110, and can also add a parallel resonance frequency F4 in the attenuation band (f4 band). In this way, the filter device 300 can increase the attenuation band in the C-type region by providing the inductor L3 in parallel, and by partially adjusting each numerical value, it can become a trap filter suited to the purpose even if the attenuation band is increased.

[0083] [Embodiment 5] In the first embodiment, an LC parallel resonator has been described in which an LC series resonator RC1 formed by connecting an inductor L1 and a capacitor C1 in series and an LC series resonator RC2 formed by connecting an inductor L2 and a capacitor C2 in series are connected in parallel as shown in Fig. 1. In the second embodiment, a filter device 110 has been described in which the inductor L1 and the inductor L2 are magnetically coupled to each other in the filter device 100 of the first embodiment as shown in Fig. 4(A). In the fifth embodiment, a filter device 400 in which a capacitor is provided in parallel with the filter device 110 of the second embodiment will be described.

[0084] FIG. 26 is a circuit diagram of a filter device 400 according to the fifth embodiment. As shown in FIG. 26, the filter device 400 includes an inductor L1, an inductor L2, a capacitor C1, a capacitor C2, and a capacitor C3 (a third capacitor). The inductor L1 and the inductor L2 are magnetically coupled to each other. The filter device before the capacitor C3 is added corresponds to the filter device 110 according to the second embodiment. In the filter device 400 according to the fifth embodiment, the same components as those in the filter device 100 according to the first embodiment and the filter device 110 according to the second embodiment are denoted by the same reference numerals and detailed description thereof will not be repeated. In the antenna device 1000 according to the first embodiment, the filter device 400 according to the fifth embodiment may be used instead of the filter device 100.

[0085] Fig. 27 is a diagram showing an example of change in reactance characteristics before and after adding capacitor C3. In Fig. 27, the horizontal axis is frequency and the vertical axis is reactance. The graph in Fig. 27(a) is an example of reactance characteristics of filter device 110 of embodiment 2 before adding capacitor C3. The graph in Fig. 27(b) is an example of reactance characteristics of filter device 400 of embodiment 5 after adding capacitor C3.

[0086] Fig. 28 is a diagram showing an example of the change in insertion loss before and after the addition of the capacitor C3. In Fig. 28, the horizontal axis is frequency and the vertical axis is insertion loss. The graph in Fig. 28(a) shows an example of the insertion loss of the filter device 110 of the second embodiment before the addition of the capacitor C3. The graph in Fig. 28(b) shows an example of the insertion loss of the filter device 400 of the fifth embodiment after the addition of the capacitor C3.

[0087] In Fig. 27, the reactance characteristic of the filter device 110 of the second embodiment is shown by a line Ln41, and the reactance characteristic of the filter device 400 of the fifth embodiment is shown by a line Ln42. In Fig. 28, the insertion loss of the filter device 110 of the second embodiment is shown by a line Ln43, and the insertion loss of the filter device 400 of the fifth embodiment is shown by a line Ln44. Specifically, the filter device 110 was simulated with an inductor L1 of 3.1 nH, an inductor L2 of 1.0 nH, a capacitor C1 of 0.4 pF, a capacitor C2 of 3.8 pF, and a coupling coefficient k of 0.5. The filter device 400 was simulated with an inductor L1 of 3.1 nH, an inductor L2 of 1.0 nH, a capacitor C1 of 0.4 pF, a capacitor C2 of 3.8 pF, a capacitor C3 of 0.4 pF, a 1 The simulation was performed with a capacitance of 0.55 pF and a coupling coefficient k of 0.5. That is, filter device 400 has the same values ​​as filter device 110, except for the value of capacitor C3.

[0088] As shown in FIGS. 27 and 28, the filter device 400 can add a new parallel resonant frequency F5 to the L characteristic region by connecting the capacitor C3 in parallel. Here, the parallel resonant frequency F3 of the filter device 400 is shifted to F3'', which is the lower frequency side of the graph, compared to the filter device 110. In this way, by adding the capacitor C3 in parallel to the filter device 110, the parallel resonant frequency F3 can be shifted to the lower frequency side. On the other hand, in order to add a new parallel resonant frequency F5 while suppressing such a shift in the parallel resonant frequency F3, each numerical value may be adjusted. The adjustment of each numerical value will be described with reference to FIGS. 29 and 30.

[0089] Fig. 29 is a diagram showing an example of change in reactance characteristics before and after adding capacitor C3. In Fig. 29, the horizontal axis is frequency and the vertical axis is reactance. The upper graph in Fig. 29 is an example of reactance characteristics of filter device 110 of embodiment 2 before adding capacitor C3. The lower graph in Fig. 29 is an example of reactance characteristics of filter device 400 of embodiment 4 after adding capacitor C3.

[0090] Fig. 30 is a diagram showing an example of the change in insertion loss before and after the addition of capacitor C3. In Fig. 30, the horizontal axis is frequency and the vertical axis is insertion loss. The upper graph in Fig. 30 shows an example of the insertion loss of filter device 110 of embodiment 2 before capacitor C3 is added. The lower graph in Fig. 30 shows an example of the insertion loss of filter device 400 of embodiment 5 after capacitor C3 is added.

[0091] In Fig. 29, the reactance characteristic of the filter device 110 of the second embodiment is shown by a line Ln41, and the reactance characteristic of the filter device 400 of the fifth embodiment is shown by a line Ln45. In Fig. 30, the insertion loss of the filter device 110 of the second embodiment is shown by a line Ln43, and the insertion loss of the filter device 400 of the fifth embodiment is shown by a line Ln46. Specifically, the filter device 110 was simulated with an inductor L1 of 3.1 nH, an inductor L2 of 1.0 nH, a capacitor C1 of 0.4 pF, a capacitor C2 of 3.8 pF, and a coupling coefficient k of 0.5. The filter device 400 was simulated with an inductor L1 of 3.1 nH, an inductor L2 of 0.38 nH, a capacitor C1 of 0.4 pF, a capacitor C2 of 10 pF, a capacitor C3 of 1.6 pF, and a coupling coefficient k of 0.5. That is, in the filter device 400, the values ​​of the inductor L2, the capacitor C2, and the capacitor C3 are changed from those in the filter device 110.

[0092] 29 and 30, by adjusting each value, the filter device 400 can make the series resonance frequency F1 in the pass band (f1 band), the series resonance frequency F2 in the pass band (f2 band), and the parallel resonance frequency F3 in the attenuation band (f3 band) similar to the frequencies of the filter device 110, and can also add a parallel resonance frequency F5 in the attenuation band (f5 band). In this way, the filter device 400 can increase the attenuation band in the L-type region by providing the capacitor C3 in parallel, and by partially adjusting each value, it can become a trap filter suited to the purpose even if the attenuation band is increased.

[0093] The filter device 110 may be configured such that an inductor L3 is added in parallel and a capacitor C3 is further connected in parallel to the inductor L3. In such a case, an attenuation band can be added in the C-type region and the L-type region. Also, the filter device 110 may be an integrated type in which the inductor L3 and the capacitor C3 are incorporated, or the filter device 110 may be a separate unit. Device Using inductor elements and capacitor elements other than 110, DeviceThe parallel resonance frequency of the filter 110 may be adjusted. Device By separating it from 110, it becomes easier to adjust the frequency to reflect the characteristics of each individual component when incorporated into the antenna device 1000.

[0094] The embodiments disclosed herein should be considered to be illustrative and not restrictive in all respects. The scope of the present disclosure is defined by the claims, not by the description of the embodiments described above, and is intended to include all modifications within the meaning and scope of the claims. [Explanation of symbols]

[0095] 100, 110, 150, 200 filter device, 155, 165 antenna, 170 substrate, 1000, 2000, 3000 antenna device, 4000 antenna module, C1, C2 capacitor, L1, L2 inductor, P1, P2 terminal, RC1, RC2 series resonator, RC3 parallel resonator, RF1, RF2 power supply circuit.

Claims

1. A filter device having a pass band of a first frequency band, a pass band of a second frequency band lower than the first frequency band, and an attenuation band of a third frequency band between the first frequency band and the second frequency band, a first series resonator that resonates in series at a first resonant frequency in the first frequency band by a first inductor and a first capacitor connected in series with the first inductor; a second series resonator that resonates in series at a second resonant frequency in the second frequency band by a second inductor and a second capacitor connected in series with the second inductor, the first series resonator and the second series resonator are connected in parallel and resonate in parallel at a third resonant frequency in the third frequency band; the second resonant frequency is lower than the first resonant frequency; the third resonant frequency is between the first resonant frequency and the second resonant frequency, The first inductor and the second inductor are magnetically coupled to each other.

2. The filter device according to claim 1 , wherein the first inductor and the second inductor are additively coupled to each other.

3. The filter device of claim 1 , wherein the first inductor and the second inductor are depolarized coupled to each other.

4. The filter device of claim 1 , wherein the first inductor is a parasitic inductance.

5. The filter device according to any one of claims 1 to 4, wherein the filter device is provided in an antenna device capable of radiating the first resonant frequency and the second resonant frequency as resonant frequencies.

6. The filter device according to any one of claims 1 to 4, wherein the filter device is configured as an integrated part.

7. 5. The filter device according to claim 1, further comprising a third capacitor or a third inductor connected in parallel to the first series resonator and the second series resonator.

8. a third capacitor or a third inductor further connected in parallel to the first series resonator and the second series resonator, the filter device includes an input terminal connected to one end of the first series resonator and one end of the second series resonator, and an output terminal connected to the other end of the first series resonator and the other end of the second series resonator, The filter device according to claim 6 , wherein the third capacitor or the third inductor is connected as a separate element between the input terminal and the output terminal.

9. a first feed circuit for inputting and outputting a high-frequency signal; a first antenna capable of radiating the first resonant frequency and the second resonant frequency as resonant frequencies; 5. An antenna device comprising: the filter device according to claim 1, which is disposed between the first feeding circuit and the first antenna.

10. An antenna module including a first antenna device and a second antenna device, The first antenna device is a first feed circuit for inputting and outputting a high-frequency signal; a first antenna capable of radiating a first resonant frequency and a second resonant frequency as resonant frequencies; a filter device disposed between the first feeding circuit and the first antenna, The filter device comprises: a pass band of a first frequency band, a pass band of a second frequency band lower than the first frequency band, and an attenuation band of a third frequency band between the first frequency band and the second frequency band, a first series resonator that resonates in series at the first resonant frequency in the first frequency band by a first inductor and a first capacitor connected in series with the first inductor; a second series resonator that resonates in series at the second resonant frequency in the second frequency band by a second inductor and a second capacitor connected in series with the second inductor, the first series resonator and the second series resonator are connected in parallel and resonate in parallel at a third resonant frequency in the third frequency band; The second antenna device is a second feed circuit for inputting and outputting a high-frequency signal; a second antenna capable of radiating the third resonant frequency as a resonant frequency, An antenna module, in which the first antenna device and the second antenna device are disposed in close proximity to each other.

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