SIMO DC-DC Converter

Abstract

The single-inductor multiple-output DC-DC converter may be configured as a buck-boost converter. The converter may include an inductor, multiple switches coupled to the inductor to control the conduction and de-conduction phases of the inductor, and multiple output rails. Each of the multiple output rails may include at least one switch configured to connect the output rail to the inductor of the buck-boost converter. Depending on the inductor conduction and de-conduction patterns and the state of the one or more switches, the various output rails may be supplied with multiple different output voltages and / or output currents. Any of multiple regulation strategies may be utilized to further control the output voltages and / or output currents.

Description

Technical Field

[0001] Various embodiments generally relate to a single inductor multiple output (SIMO) direct current (DC)-DC converter and its implementation and use.

Background Art

[0002] In modern computing applications, including but not limited to wireless, various supply voltages for various applications and / or functions are required within the same integrated circuit (IC) that can be independently powered on and off. For maximum efficiency, this requires the creation of multiple power islands within a single IC. As modern devices increase in complexity, cost and size savings become essential elements in power management design. Ideally, each power island would have its own DC-DC converter to provide maximum efficiency in power supply. This would require many large and expensive discrete components, especially off-chip inductors. Modern devices generally use switched-mode power supplies to efficiently convert a first DC voltage to a second DC voltage. However, many devices include multiple electronic components with multiple different voltage requirements. These different voltage requirements can be satisfied by using multiple switched-mode DC-DC converters, which may be impractical or undesirable. For example, switched-mode DC-DC converters generally use inductors for voltage conversion, and it may be desirable to reduce the number of inductors required for a given application, considering cost and space. Alternatively, various forms of gate charge sharing methods or high-power efficiency single-input multiple-output converters or systems using switching converters can be used.

[0003] In the drawings, the same reference numerals generally refer to the same parts throughout different figures. The drawings are not necessarily drawn to scale, and emphasis is placed on explaining the principles of the present invention. In the following description, various embodiments of the present invention are described with reference to the following drawings.

Brief Description of the Drawings

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[0005] The following detailed description refers to the accompanying drawings which show, by way of example, specific details and embodiments in which the invention may be practiced.

[0006] The term "exemplary" as used herein means "serving as an example, instance, or illustration." Any embodiment or design described herein should not necessarily be construed as preferred or advantageous over other embodiments or designs.

[0007] As used herein, the word "over" with respect to a deposited material formed "over" a side or surface may mean that the deposited material may be formed "directly over" the underlying side or surface, e.g., in direct contact. The word "over" with respect to a deposited material formed "over" a side or surface may also mean that the deposited material may be formed "indirectly over" the underlying side or surface with one or more additional layers disposed between the underlying side or surface and the deposited material.

[0008] The SIMO converter may utilize a linear regulator to dynamically supply a regulated output voltage within a predefined range for the converter output in question. The regulator may receive an input voltage and dynamically regulate one or more output voltages within a predefined range. The regulator may be able to regulate one or more output voltages to stay within their predefined range, while the SIMO switch is configured to supply the output voltage to the SIMO output section.

[0009] Electronic devices are increasingly being exposed to ever-growing demands, such as miniaturization, improved connectivity, increased processor speed, and improved battery life. Among other things, these demands require a robust power management function that can be implemented in small devices at least in some situations while maintaining cost competitiveness. The SIMO architecture is suitable for these demands to extend the battery life of products with high energy efficiency and space constraints. The SIMO architecture is also an excellent candidate for wearable, wearable, sensors, smart home hubs, etc. because it functions properly even in an ultra-low power environment.

[0010] The SIMO architecture is also suitable for meeting another requirement commonly recognized in such devices, namely the requirement to supply power to multiple devices or circuits with different voltage or current requirements (e.g., 2.5V, 5V, 10V, etc.). The SIMO architecture may be employed in connection with a DC-DC converter having multiple output rails (e.g., a buck-boost converter). Using the principles and methods described herein, a buck-boost converter using SIMO can be configured to generate multiple different output voltages and / or currents. The generated voltage and / or voltage can then be applied to any of the multiple output rails using multiple switches. In this way, a single DC / DC converter using SIMO technology can generate multiple power outputs to supply power to multiple components (e.g., one or more processors, motors, one or more speakers, etc.) within devices having various power requirements (e.g., wearables, wearables, sensors, smart home hubs, etc.).

[0011] A SIMO buck-boost converter can be configured to output one or more desired voltages or currents at any of a plurality of output rails. That is, a SIMO buck-boost converter can be configured to output n different voltages or currents on n output rails, or alternatively, to output less than n different voltages or currents on n output rails. As described in more detail below, a SIMO buck-boost converter may change a selected voltage or current to be output on a given rail. This is illustrated, for example, by four output rails in FIG. 2, but the number of rails is not limited to four and can be selected to be more or less than four depending on the implementation requirements. For example, a SIMO buck-boost converter may be required to supply power to a plurality of components having different voltage and / or current requirements, and the number of rails may be selected based on the number of different voltage / current requirements of the components. These concepts may apply to any of the SIMO buck-boost converter configurations disclosed herein or to any other aspect of the present disclosure.

[0012] As an extension of these concepts, the SIMO architecture can provide beneficial advantages to wireless communication devices or devices with wireless communication capabilities. Computing devices with wireless capabilities, such as laptops, smartphones, and tablet computers, are ubiquitous and are subject to the above requirements for miniaturization, speed, functionality, and improved battery life. Furthermore, wireless communication capabilities are being newly added to an increasing number of devices (e.g., Internet of Things (IoT) devices). Such wireless communication capabilities often include a variety of other components (e.g., data processing circuits (using, for example, an ADC), sensors, transceivers / power amplifiers, system-on-chip (SoC) applications), each with its own stringent power requirements, and often in the ultra-low power range, the number of devices requiring a high level of power efficiency is increasing. The SIMO architecture is suitable for meeting the power efficiency needs of these devices. Furthermore, considering that many such devices require multiple different voltages and / or currents for each component, the SIMO architecture in the context of a buck-boost DC-DC converter with multiple outputs is an excellent option for providing efficient power management of limited power resources (e.g., a small lithium battery) while powering devices with multiple different voltage and / or current requirements.

[0013] The SIMO converter may be configured as a SIMO system. As will be described in more detail later, the SIMO (e.g., an inductor and multiple outputs) may be configured as a DC-DC converter such as a buck-boost converter. One or more output rails of the converter may include one or more regulators (e.g., one or more linear regulators, one or more push-pull regulators, one or more low-dropout regulators, or any combination thereof), which may be configured to regulate voltage and / or current for each output rail. Each or any of the SIMO and the regulators may include additional components for its operation (e.g., one or more controllers, adders, amplifiers, comparators, logic gates, etc.). The SIMO system may include the SIMO together with either the components of the DC-DC converter, the components of one or more regulators, and / or additional components for the operation and / or regulation of the SIMO.

[0014] FIG. 1 illustratively shows a block diagram of a SIMO converter or a SIMO converter architecture or a SIMO system (which may hereinafter also be referred to as "SIMO" or the system or the SIMO circuit). SIMO, according to at least one aspect described in the present disclosure, may include an input terminal 102, a SIMO buck-boost converter 104, a push-pull regulator, a linear regulator (e.g., a low-dropout regulator (also referred to as an LDO), and / or regulators 106a-n that may include a voltage regulator, and output voltages 108a-n. The input terminal 102 may be electronically coupled to the terminals of the SIMO converter 104. Each of the regulators 106a-n may be electronically coupled to an output portion associated with each of the plurality of output portions of the SIMO converter 104. The regulators 106a-n may regulate the plurality of output voltages 108a-n (thereby providing supplies of different voltage domains for different electrical loads). The regulators 106a-n may be linear regulators. As shown in FIG. 1, the (e.g., linear) regulators 106a-n may be connected in series with the SIMO converter 104 with respect to the input terminal 102.

[0015] Different electronic devices electronically or operably coupled to one or more of the SIMO converter output rails may require different input voltages corresponding to a predefined voltage range supplied at each output rail (also referred to as an output or converter output line, for example). As an example, the SIMO converter may be electronically coupled to a transmitter, a USB port, a Wi-Fi module, a Bluetooth® chip, etc. It should be noted that other electronic devices may be coupled to the SIMO converter. Further, different technologies, such as even different types of transistors (thin film oxide transistors vs. thick film oxide transistors), may require different voltage domains supplied by the SIMO. All of these devices or technologies may have different requirements with respect to their respective supply voltages, for example, and also the ripple of the supply voltage. The SIMO must meet all the requirements of the connected electronic devices to which it is coupled. The SIMO must be as robust, simple, inexpensive, flexible, and reliable as possible.

[0016] In addition to the power requirements of various device components, some devices and / or some device components may be configured to operate according to one or more operating states, and the operating states may also accommodate various power requirements. For example, various devices and / or one or more components of various devices may operate in any of a plurality of active modes, a plurality of inactive modes, a plurality of standby modes, a plurality of sleep modes, or otherwise. These modes may accommodate various current consumption and / or voltage requirements. Further, the devices and / or their components may need to switch quickly between operating modes. For example, a transceiver can switch between a listen mode (e.g., an active mode) and a non-listen mode (e.g., an inactive mode or a standby mode) many times per second. Thus, a power management solution for such devices and / or components must be configured to respond quickly to changing power requirements and / or to vary its power output according to the predicted power needs of the components. The SIMO buck-boost converter described herein is well-suited to these requirements.

[0017] Accordingly, a wide variety of challenges must be addressed in this technical field. By way of example, a SIMO should be able to supply several voltages with low voltage ripple and / or must be flexible enough to suit a wide variety of loads and / or must be small and energy efficient enough to fit even in devices with a small form factor such as smartphones or other wearable electronic devices.

[0018] As an example, each device may require a different input voltage to operate. For example, a Bluetooth Low Energy (BLE) device may require an input voltage between 1.8V and 3.6V. The SIMO converter output voltage rail coupled to the BLE device may be associated with a predefined range of its switching output voltage that matches the input voltage requirements of the BLE device. The predefined range may also be narrowed to ensure that the voltage falls within the predefined range. This may be necessary when the switching output voltage is likely to be affected by noise.

[0019] Furthermore, the Wi-Fi module may operate best at 3.3V, but can operate within a predefined range of 1.7V to 3.6V. The SIMO converter output voltage rail connected to the Wi-Fi module may be configured such that the predefined range is smaller to ensure optimal operation of the Wi-Fi module. Each of these output voltage rails may be configured to operate independently of each other, or simultaneously or in parallel based on the voltage requirements of a given connected device for a predetermined period based on functional or application requirements.

[0020] Furthermore, a USB port or a micro-USB port may be configured to receive a 5V input voltage. However, a device plugged into the USB port may operate within a certain input voltage range. For example, a micro-USB fan plugged into the USB port may operate within an input voltage range of 4.45V to 5.25V. Therefore, the predefined range for the SIMO converter output rail associated with the USB port may be larger than the exact 5V defined for the USB port.

[0021] Examples of input voltage requirements may include: [Table 1]

[0022] Various aspects of the present disclosure are directed to improving SIMO for one or more of the above problems, or for one or more of the problems described in more detail below.

[0023] According to one aspect of the present disclosure, a switch controller may control switches in a SIMO converter to supply a switching output voltage within a voltage domain of an electronic device coupled to a converter output during a separated inductor period.

[0024] FIG. 2 shows an exemplary block diagram of a SIMO converter 104 according to some aspects in more detail. The SIMO converter 104 may include a plurality of switches as shown (the example shown implements a buck-boost converter, and it should be noted that the switch structure may vary when implementing another type of SIMO converter, such as a SIMO boost converter, or any other desired type of SIMO converter). For simplicity, the transistors within the switches are not shown. It should be understood that each switch may include a transistor or may be implemented by a transistor. For example, switch 206 may be electronically coupled between the input terminal of inductor 202 and input terminal 102. Switch 208 may be electronically coupled between the input terminal of inductor 202 and a reference potential, such as ground. Switch 210 may be electronically coupled between the output terminal of the inductor and a reference potential, such as ground. Switches 204a - n may be electronically coupled between the output terminal of inductor 202 and the plurality of output portions of SIMO 104.

[0025] One or more switch controllers, not shown in FIG. 2, can control the switches. For example, the switch controller can control switches 204a - n to control the voltage ripple of a certain switching output voltage among the switching output voltages 108a - n supplied to the relevant outputs of the output of the SIMO converter 104. Further, the controller can control to close power switches 206 and 210 to energize inductor 202. The controller can control those switches to remain closed for a predetermined period or until the inductor 202 reaches a predefined energy level. Further, the controller can control to close switch 208 and one of switches 204a - n to supply one of the output voltages 108a - n to the output terminals 110a - n. The controller can control those switches to remain closed for a predetermined period or until a defined output voltage is reached.

[0026] Switches 204a - n, 206, 208, and 210 may be controlled independently and / or collectively by one switch controller, independently by individual switch controllers, or in any combination thereof. Further, switches 204a - n, 206, 208, and 210 may all be part of the same circuit or individual circuits.

[0027] Although FIG. 2 is shown as including an inductor, the SIMO buck-boost converter 104 may optionally be configured without an inverter, according to various aspects of the present disclosure. In this configuration, the SIMO buck-boost converter 104 may receive the output voltage or current of an external inductor, which in this particular implementation is not considered part of the SIMO buck-boost converter. In this configuration, the output voltage or current of the inductor may be applied to any of one or more output terminals through switches 204a - n, and the output voltage or current may be regulated as otherwise described herein. In this manner, the SIMO buck-boost converter 104 may be configured as an integrated circuit or chip. According to some aspects of the present disclosure, in an implementation where the SIMO buck-boost converter is configured as an integrated circuit or chip that does not include an inductor as part of the converter, the SIMO buck-boost converter may include one or more switch controllers and / or one or more switches (e.g., switches 208 and 210 or any other switches described herein for controlling the duty cycle of the inductor) to control the energizing and de-energizing phases of the inductor as described herein.

[0028] FIG. 3 illustratively shows a SIMO converter 104 with push-pull linear regulators 302a - n that may include a push-pull linear regulator and / or a voltage regulator, according to some aspects. The push-pull regulators 302a - n may be the regulators 106a - n of FIG. 1. As shown in FIG. 3, the push-pull regulators 302a - n may be connected in parallel with each other and / or implemented in parallel with the SIMO buck-boost converter 104 with respect to the input terminal 102.

[0029] FIG. 4 depicts a detailed block diagram of a regulator according to some aspects. For example, the regulator 106a of FIG. 1 may be a push-pull regulator 302a. As shown in FIG. 4, the push-pull regulator 302a may be electronically coupled to the input terminal 102 and the output of the SIMO converter. The push-pull regulator 302a may regulate a target output voltage of 405a V O1 The push-pull regulator 302a may include comparators (e.g., a first comparator 404 and a second comparator 406) that compare the low reference voltage and the high reference voltage with the output voltage at the associated output (e.g., the associated output rail of the SIMO converter), respectively. For simplicity, only one push-pull regulator 302a is shown. In some aspects of the present disclosure, a plurality of push-pull regulators may be included to regulate different output voltages. In this case, exactly one of the plurality of push-pull regulators may be assigned to each of the plurality of outputs of the SIMO converter. Further, in various aspects of the present disclosure, for each of the plurality of outputs of the SIMO converter, only one comparator may be provided. Thus, in some implementations, one or more outputs may include exactly one comparator 404 for comparing the output voltage at the associated output with the low reference voltage. Further, in some implementations, one or more outputs may include exactly one comparator 406 for comparing the output voltage at the associated output with the high reference voltage. Additionally, any type of hybrid implementation with one or more comparators per output of the SIMO converter may be provided.

[0030] The push-pull regulator 302a may also include switches 408 and 410. The voltages fed forward from the first comparator 404 and the second comparator 406 may be used to control the switches 408 and 410. When the output voltage 405a is below the low reference voltage (which may be applied to the non-inverting input of the first comparator 404), the first comparator 404 may close the switch 408 to regulate the output voltage and raise it within a predefined voltage range. When the output voltage 405a exceeds the high reference voltage (which may be applied to the inverting input of the second comparator 406), the second comparator 406 may close the switch 410 to regulate the output voltage and push it down within a predefined voltage range. When the output voltage 405a is within the predefined range, the switches 408 and 410 remain open and the regulator 302a does not regulate the output voltage.

[0031] The comparators 404 and 406 may receive the low reference voltage and the high reference voltage respectively. The low reference voltage and the high reference voltage set the lower and upper limits of a predefined range of the output voltage. While the SIMO output voltage is within the predefined range, the regulator 302a is not operating, improving the efficiency of the system 400.

[0032] The regulator 302a operates when the SIMO output voltage goes out of the predefined range. When the output voltage 405a is higher than the high reference voltage, the regulator 302a may activate a sink circuit to regulate the output voltage 405a within the predefined range. When the output voltage 405a is lower than the low reference voltage, the regulator 302a may activate a source circuit to regulate the output voltage 405a within the predefined range.

[0033] Operating the regulator 302a is less efficient than operating the SIMO converter and should be minimized. For outputs where efficiency is important (efficiency is more important than ripple or regulation), the predefined range may be set large to reduce the operation of the push-pull regulator. For outputs where ripple is important (ripple is more important than efficiency), the predefined range may be set small to regulate the output voltage more precisely. For fast loop / overshoot, the low reference voltage can be made higher to protect from fast loops, or the high reference voltage can be made lower for fast overshoot.

[0034] Dynamic programming within a predefined range may also be possible. This is necessary when different load activities may occur at one SIMO output. That is, operating the regulator 302a may be operable within a plurality of predefined ranges, and these predefined ranges may be selected using any of at least a predefined timing, an on-demand response, or the use of an adaptive selection. In a timing-based selection, the predefined range for operating the regulator 302a (or the predefined range of any regulator on any output rail) may be selected based on a predefined timing (e.g., a first predefined range for a first duration, a second predefined range for a second duration, a third predefined range for a third duration, etc.). This predefined timing selection may be used in a wide range of implementations, and one such implementation may be when a component is expected to switch operating modes (e.g., modes with different current and / or voltage requirements) in a known schedule. In this way, the predefined timing may be selected to correspond to the current and / or voltage requirements corresponding to the operating mode. According to other aspects, the predefined range may be selected based on an on-demand request. In this way, one or more components (e.g., a controller) for selecting the predefined range may be configured in a feedback loop to receive measurements of the current drawn by the load, the voltage across a known resistance, or other sources of information for identifying one of a plurality of predefined settings corresponding to the current and / or voltage requirements of the load. Using this information, one or more components for selecting the predefined range may select a corresponding predefined range that satisfies the requirements of the load. According to other aspects, the predefined range may be selected adaptively. In this way, one or more processors may be configured to predict the power requirements using one or more calculations and adapt accordingly.Therefore, one or more processors may receive the power demand of the output rail (e.g., the drawn current, the voltage across a known resistance, etc.), compare this information with the past power demands of the rail and / or the load, and identify the possible next power demand. One or more processors may be configured to recognize one or more patterns of power demand and identify the possible next power demand based on the current power demand and / or one or more recent power demands. One or more processors may be configured to execute one or more artificial neural networks or other artificial intelligence, whereby, in light of past power demand information, an adaptively selected predefined range may be selected based on the current power demand and / or one or more recent power demands.

[0035] In some aspects of the present disclosure, switch 410 may be connected to ground or any other reference potential. Further, push-pull regulator 302a may include other elements not shown in FIG. 4.

[0036] FIG. 5 illustratively shows a flowchart of a method of operating a SIMO converter according to some aspects. Method 500 includes supplying a switched output voltage in response to an input voltage applied to an inductor 502. SIMO includes a plurality of switches, and the plurality of switches may include a first switch coupled between a first terminal of the inductor and the input voltage, a second switch coupled between the first terminal of the inductor and the reference potential, and a third switch coupled between a second terminal of the inductor and the reference potential. The method may further include controlling the plurality of switches to control the switched output voltage 504, dynamically setting a predefined target output voltage specific to each associated regulator 506, and regulating the switched output voltage to remain within a predefined range from the target output voltage using the input voltage 508.

[0037] FIG. 6 illustratively shows a flowchart of a method of operating a SIMO according to some embodiments. Method 600 includes controlling a switching stage including an inductor and a plurality of switches to provide a switching output voltage in response to an applied input voltage depending on the switching states of the plurality of switches 602. The plurality of switches may include a first switch coupled between a first terminal of the inductor and the input voltage, a second switch coupled between the first terminal of the inductor and a reference potential, and a third switch coupled between a second terminal of the inductor and the reference potential. The method may further include dynamically setting an output voltage in response to receiving the switching output voltage 604, determining at least one of whether the switching output voltage exceeds a predefined upper threshold voltage greater than a target regulator output voltage or whether the switching output voltage is less than a predefined lower threshold voltage less than the target regulator output voltage 606, and regulating the switching output voltage using the input voltage 608.

[0038] FIG. 7 shows a detailed block diagram of an exemplary system 700 including a regulator according to some embodiments. For example, the regulator 106a of FIG. 1 may be a digital push-pull regulator 702a. As shown in FIG. 7, the digital push-pull regulator 702a may be electronically coupled to the input terminal 102 and the output of the SIMO converter. The digital push-pull regulator 702a has a target output voltage V O1It may be regulated. The digital push-pull regulator 702a may include digital gate controllers (e.g., the first digital gate controller 704 and the second digital gate controller 706) that respectively compare the low reference voltage and the high reference voltage with the output voltage at the associated output (e.g., the associated output rail of the SIMO converter). For simplicity, only one digital push-pull regulator 702a is shown. In some aspects of the present disclosure, a plurality of push-pull regulators may be included to regulate different output voltages. In this case, exactly one of the plurality of digital push-pull regulators may be assigned to each output of the plurality of outputs of the SIMO converter. Further, in various aspects of the present disclosure, for each output of the plurality of outputs of the SIMO converter, only one digital gate controller may be provided. Thus, in some implementations, one or more outputs may include exactly one digital gate controller 704 for comparing the output voltage at the associated output with the low reference voltage. Further, in some implementations, one or more outputs may include exactly one digital gate controller 706 for comparing the output voltage at the associated output with the high reference voltage. Further, any type of hybrid implementation with one or more comparators for each output of the SIMO converter may be provided.

[0039] The digital push-pull regulator 702a may also include switches 708 and 710. Voltages fed forward from the first gate controller 704 and the second gate controller 706 may be used to control the switches 708 and 710. The output voltage V O1 When it is below the low reference voltage (which may be applied to the non-inverting input of the first gate controller 704, e.g., a comparator), the first gate controller 704 may close one or more switches 708 to regulate the output voltage and raise it within a predefined voltage range. The output voltage V O1When it exceeds the high reference voltage (which may be applied to the inverting input of the second digital gate controller 706, for example, a comparator), the second digital gate controller 706 may close one or more switches 710 to regulate the output voltage and push it down within a predefined voltage range. When the output voltage 405a is within the predefined range, the switches 708 and 710 remain open, and the regulator 302a does not regulate the output voltage.

[0040] The SIMO system may regulate the output voltage by a digital push-pull regulator and an analog push-pull regulator. The digital push-pull regulator may regulate the output voltage using a plurality of power switches (708 and 710). The analog push-pull regulator may regulate the output voltage by the gate voltage of the switches (408 and 410).

[0041] In a system including a SIMO converter, the regulator may operate to dynamically set the output voltage within a predefined range for a target SIMO output. The SIMO converter may include an input terminal for charging an inductor. The switch connected between the input terminal and the input terminal of the inductor is closed together with the switch connected to the output terminal of the inductor and ground to energize the inductor. When energized, the SIMO may include a switch and a switch controller to supply the output voltage from the energized inductor to the output. The regulator may regulate to keep the output voltage within its predefined range while the switch supplying the output is closed (on). The regulator may regulate the output voltage using the input voltage from the input terminal. Using the input voltage to regulate the output voltage (e.g., using a first comparator) enables fast regulation of the output voltage to re-enter its predefined range when the output voltage goes out of the predefined range (e.g., predefined by a low reference voltage). Further, using a reference potential such as the ground potential to regulate the output voltage (e.g., using a second comparator) also enables fast regulation of the output voltage to re-enter its predefined range when the output voltage goes out of the predefined range (e.g., predefined by a high reference voltage).

[0042] Regulators connected to the input and output terminals of the SIMO may be used to regulate the output voltage of each output terminal (or output rail). Using the input voltage from the input terminal, the regulator can keep the output voltage within its predefined range while the switch connected to the output is closed.

[0043] The inductor may be implemented on a different chip from the switches of the SIMO and the linear regulator. The switches of the SIMO and the linear regulator may be implemented on the same chip.

[0044] The plurality of switches may be electronically or operably coupled between or to the output terminals of the inductor and the output of the SIMO. An additional switch may be electronically coupled between the output and input terminals of the inductor.

[0045] The SIMO system may include a capacitor electronically or operably coupled between or to the output voltage and a reference potential such as ground. Each capacitor may have a configurable capacitance range. The capacitance range may vary for different output voltages.

[0046] The inductor of the SIMO system may have a dynamically configurable inductance range. Further, the SIMO may be configured, for example, as a buck converter, to output a voltage lower than the input voltage. Alternatively, the SIMO may be configured, for example, as a boost converter, to output a voltage that matches the load voltage.

[0047] As described above, the regulator used to regulate the output voltage may be configured as a push-pull regulator. The regulator may use a switch electronically coupled between the input voltage and the output voltage to regulate the output voltage within its predefined range. Further, the regulator may use one or more comparators to regulate the output voltage.

[0048] For example, the regulator may include a low reference comparator and a high reference comparator. When the output voltage falls below its respective predefined range, the switch controller may control the switch between the input voltage and the output voltage to raise the output voltage within its predefined range.

[0049] When the output voltage exceeds its respective predefined range, the switch controller may control the switch between the output voltage and a reference potential such as ground to lower the output voltage within its predefined range. Alternatively, the switch may be between the input voltage and the reference potential.

[0050] The regulator may also include a capacitor electronically coupled between the switching output voltage and a reference potential such as ground. The capacitor may be dynamically configured to have a predefined capacitance range.

[0051] Various implementations of the hysteretic comparator are possible. For example, the hysteretic comparator can be configured by an intentional mismatch between pairs of input portions of transistors. This implementation eliminates additional power losses. However, this can greatly vary the hysteresis voltage and affect the voltage offset.

[0052] As another example, the hysteretic comparator may be configured to receive current injection at one of the input portions of the transistor. This implementation allows for precise control of the hysteresis voltage and does not affect the voltage offset. However, it requires the addition of extra circuitry and extra current. Further implementations of the hysteretic comparator other than those described above are possible.

[0053] The output switch of the SIMO converter 104 may be configured to operate either as an on / off switch or as a linear regulator. The switch may operate as an on / off switch to supply the switching output voltage at the corresponding converter output. Further, the switch may operate as a linear regulator to regulate the switching output voltage at different converter outputs.

[0054] EFFICENC IS ONE THING; BUT ALS NEED WITH DIFFERNE LAOD ON NEIBORING RAILS: CAN LEAR TO CROSS-REGULATING: NEEE DTO CHANGE CAN BE CHANGED THOUGHT

[0055] FIG. 8 shows a block of an exemplary system 800 that includes a SIMO converter 104 in accordance with at least one aspect described in the present disclosure. In some aspects of the present disclosure, the SIMO converter 104 may correspond to the SIMO converter 104 described elsewhere in the present disclosure. In some aspects of the present disclosure, the SIMO converter 104 may include multiple output portions to supply switching output voltages 108a - n at different values at two or more of the converter output portions (or output rails or output voltage rails). In some aspects of the present disclosure, the system 800 may include one or more low dropout regulators (also referred to as LDOs) (not shown). In some aspects of the present disclosure, the LDO may correspond to the regulator 106 described elsewhere in the present disclosure.

[0056] The switches 204a - n (e.g., secondary switches 204a - n) may each include at least one transistor. The transistor may be configured to operate in a first operating mode or a second operating mode. In the first operating mode, the corresponding switch 204a - n may operate as an on / off switch. For example, the switch 204a - n may transition between an open state (e.g., non - conducting state) and a closed state (e.g., conducting state). In the first operating mode, the system 800 may operate as a hybrid SIMO converter as discussed elsewhere in the present disclosure.

[0057] In the second operating mode (shown in FIG. 8), one or more of the secondary switches 204b - n (shown in FIG. 8) can operate as a regulator, and one or more of the secondary switches 204a (shown in FIG. 8) can operate as an on / off switch. The secondary switch 204a is shown in FIG. 8 as being on for simplicity of discussion and illustration.

[0058] In some aspects of the present disclosure, one or more of the transistors of switches 204a - n may operate in a linear region (e.g., active region) and may operate as a regulator. In FIG. 8, the secondary switches 204b - n are shown as regulators for simplicity of discussion and illustration. When operating switches 204b - n as regulators, one terminal (source) may receive the switched output voltage at the output terminal of inductor 202. The other terminals (drains) of switches 204b - n may be connected to the associated output terminals 110b - n that supply output voltages 108a - n. The other terminals of switches 204b - n may be connected to the input of a comparator, and the comparator may compare the potential at the other terminals of switches 204b - n with a reference voltage. The output of the comparator may be connected to the gates of switches 204b - n to drive switches 204b - n in the linear region. In a second operating mode, in some aspects of the present disclosure, system 800 may operate as a single input single output (SISO) converter. In some aspects of the present disclosure, in the second operating mode, the first secondary switch 204a may operate in a closed state (e.g., on position), and the remaining secondary switches 204b - n may operate as regulators. In these and other aspects of the present disclosure, for the remaining secondary switches 204b - n, one or more LDOs may set the target output voltage specific to the associated regulator. Alternatively, for the remaining secondary switches 204b - n, one or more of the remaining secondary switches 204b - n may regulate the switching output voltage at the first converter output to the associated regulator-specific target output voltage set from the first converter output V O1 may set the associated regulator-specific target output voltage from 108a.

[0059] FIG. 9 shows a flowchart of an exemplary method 900 for operating a switched converter in accordance with at least one aspect described in the present disclosure. Method 900 may include one or more of blocks 902, 904, 906, 908, or 910. Although shown as separate blocks, the operations associated with one or more of the blocks of method 900 may, depending on a particular implementation, be divided into additional blocks, combined into fewer blocks, or removed.

[0060] In block 902, the method may include controlling a switch. In some aspects of the present disclosure, the method may include controlling the switch to control a switching output voltage. In these and other aspects of the present disclosure, the method may include controlling the switch to apply the switching output voltage to a converter output.

[0061] In block 904, the method may include dynamically setting a regulator-specific target output voltage associated with each. In some aspects of the present disclosure, the method may include dynamically setting a regulator-specific target output voltage associated with each to a respective converter output.

[0062] In block 906, the method may include selecting an operating mode of the converter. In some aspects of the present disclosure, the method may include selecting the operating mode of the converter from a first operating mode or a second operating mode.

[0063] In block 908, the method may include operating the converter as a single inductor multiple output converter. In some aspects of the present disclosure, the method may include operating the converter as a SIMO converter in a first operating mode.

[0064] In block 910, the method may include operating the converter such that the switching output voltage is regulated for at least one converter output, and for at least one output, its series switch is always ON / conductive and is regulated by a primary switch that functions as a primary SISO output. In some aspects of the present disclosure, the converter may operate such that for at least one converter output, the corresponding secondary switch is always operating in the closed position and the switching output voltage at the corresponding converter output is regulated by another secondary switch operating as a regulator. In these and other aspects of the present disclosure, the method may include operating the converter such that the switching output voltage is regulated for at least one converter output.

[0065] Modifications, additions, or omissions may be made to method 900 without departing from the scope of the present disclosure. For example, the operations of method 900 may be performed in a different order. Additionally, or alternatively, two or more operations may be performed simultaneously. Further, the operations and actions described are provided by way of example only, and some of the operations and actions may be optional, combined into fewer operations and actions, or extended to additional operations and actions without departing from the essence of the described aspects.

[0066] An electronic device electrically or operably coupled to the converter output may include different input voltages or input voltage optimization settings. In some aspects of the present disclosure, one or more electronic devices may include a high efficiency setting, while other electronic devices may include a regulation setting for high noise and switching output voltage. In some aspects of the present disclosure, operating a DC-DC converter (e.g., system 800) as a SIMO converter may supply a switching output voltage (e.g., an input voltage for an electronic device) with high efficiency. In these and other aspects of the present disclosure, operating a DC-DC converter as a SISO including a switch operating as a regulator may reduce noise and improve regulation of the switching output voltage (e.g., cross-regulation).

[0067] In some aspects of the present disclosure, one or more of the secondary switches may operate in two or more operating modes. In these and other aspects of the present disclosure, the first operating mode of the secondary switch may include an on / off operating mode. In these and other aspects of the present disclosure, the second operating mode of the secondary switch may include a regulation operating mode. In the second operating mode, the secondary switch between the inductor and the first converter output can operate as an on / off switch, and one or more of the other secondary switches can operate as a regulator. Operating the secondary switch in either the first operating mode or the second operating mode may enable the system to operate as a SIMO converter or as a SISO converter.

[0068] In some aspects of the present disclosure, the secondary switch may include a plurality of transistors. In these and other aspects of the present disclosure, the transistors of the secondary switch may be configured to operate in a saturation region or an active / linear region. During operation in the saturation region, the transistor may operate as an on / off switch. The operation of the transistor as an on / off switch may enable (e.g., conduct) or block (e.g., not conduct or stop or mute) current from propagating through the transistor. During operation in the linear region, the transistor may operate as a regulator. The operation of the transistor as a regulator may cause the transistor to regulate the switching output voltage at one or more of the converter outputs.

[0069] In some aspects of the present disclosure, the transistors of the secondary switch operating as a regulator may operate as a linear regulator. In other aspects of the present disclosure, the transistors of the secondary switch operating as a regulator may operate as a digital regulator.

[0070] In some aspects of the present disclosure, one or more processors may control the operation of the system. In these and other aspects of the present disclosure, the processor may select an operation mode of the system (e.g., a first operation mode or a second operation mode). In the first operation mode, the secondary switch can operate as an on / off switch, and the system can operate as a SIMO converter as discussed elsewhere in the present disclosure. In the first operation mode, the secondary switch may operate in a cut-off region (e.g., a non-conducting state) or a saturation region (e.g., a conducting state). In the second operation mode, the transistors of the secondary switch may operate as an on / off switch or a regulator.

[0071] In the second operating mode, the transistor of the first secondary switch between the inductor and the first converter output can operate as an on-switch. In these and other aspects of the present disclosure, in the second operating mode, the first secondary switch can supply a switched output voltage (e.g., the first secondary switch can be defined as the main output voltage of the SISO converter).

[0072] In some aspects of the present disclosure, in the second operating mode, the transistors of one or more of the other secondary switches can operate as on-switches, and the transistor of the first secondary switch can operate as a regulator. Further, in some aspects of the present disclosure, the transistors of more than one secondary switch may operate as on-switches simultaneously.

[0073] In some aspects of the present disclosure, the system (e.g., the converter) may operate in the second operating mode such that at least one converter output is regulated. The transistor of the secondary switch of the converter output to be regulated can operate as an on-switch. Further, the transistors of one or more other secondary switches may operate as regulators and can set the output voltage (e.g., the switched output voltage) to a regulator-specific target output voltage.

[0074] In some aspects of the present disclosure, exactly one converter output of the system can be regulated. In these and other aspects of the present disclosure, for the other converter outputs, the regulator may dynamically set the associated regulator-specific target output voltage.

[0075] In some aspects of the present disclosure, the converter output may be regulated using the transistors that make up the corresponding secondary switch. In these and other aspects of the present disclosure, the transistors can operate as regulators in the linear region. In some aspects of the present disclosure, one or more of the converter outputs may be regulated by operating the corresponding transistors in the saturation region.

[0076] In some aspects of the present disclosure, one or more of the transistors of the secondary switch may operate as a linear regulator. In these and other aspects of the present disclosure, one or more of the transistors of the secondary switch may operate as a digital regulator.

[0077] Accordingly, one or more aspects described in the present disclosure may supply a switching output voltage (e.g., a single device may supply a switching output) with different values and settings for electronic devices including different levels of efficiency and regulation settings.

[0078] As described above, one problem in a SIMO architecture or SIMO converter is cross-regulation. Cross-regulation can be understood as a change in the output voltage of a multi-voltage power supply when a change in the output voltage occurs due to a load change on one or more output voltage rails of a SIMO converter (which may include multiple output rails). The noise resulting from such cross-regulation in a regulated output power supply perturbation can translate into output voltage ripple on one or more other output voltage rails. Various components and / or loads may not be able to tolerate such ripple, and generally, it may be desirable to avoid, minimize, or reduce such ripple.

[0079] The output voltage ripple due to cross-regulation noise can be reduced or mitigated, or even eliminated, by configuring two or more SIMO output rails with one or more parallel push-pull regulators. When such parallel push-pull regulators are present on two or more SIMO output rails, such a configuration can be further extended to have parallel regulators with an improved power supply rejection ratio (PSRR) supplied in series by other SIMO output rails such as a higher voltage output.

[0080] PSRR, also known as the supply voltage rejection ratio, can be understood as the ability of an electronic circuit to suppress power supply variations with respect to the output signal. PSRR can be defined as the ratio of the change in the power supply voltage to the equivalent (differential) output voltage it generates. Such an output voltage depends on the feedback circuit, similar to the case of a normal input offset voltage.

[0081] This configuration having parallel push - pull regulators between the rails (one push - pull regulator can be provided between each two output rails for different output voltages) can result in improved efficiency and / or reduced size. This configuration is expected to improve output supply regulation and reduce cross - regulation of noise - sensitive outputs, especially in the analog / RF domain.

[0082] According to some aspects of the present disclosure, it may be desirable to obtain the equalization current of the regulator from one of the plurality of output rails rather than from the input terminal (e.g., V IN ). Similarly, it may be desirable for the regulator to regulate by shunting current from one output rail to another. By using either or both of these concepts (receiving equalization current from other output rails or shunting current to other output rails), the overall efficiency can be improved compared to receiving equalization current from the input terminal or shunting current to ground. These concepts may be implemented in a single output rail or any combination of rails as needed.

[0083] FIG. 10 shows an exemplary SIMO circuit according to an aspect of the present disclosure. In this circuit, a single inductor 1002 is coupled to a plurality of switches 1004 (S O1 to S O4It is represented as follows. ) are connected to a plurality of converter output lines 1006 (also referred to as converter output rails or converter output voltage rails) via. The switch controller may be configured to control the switches. Then, the switches can control the switching output voltage by switching one or more of the plurality of switches on or off according to the control by the switch controller based on the output voltage requirements for a predefined period.

[0084] According to this aspect of the present disclosure, at least two of the output lines can be connected by at least one regulator 1008. The regulator 1008 may include or be a linear regulator. At least one regulator may be configured to dynamically set a predefined target output voltage specific to the associated regulator on the associated converter output line among the plurality of converter output lines. At least one linear regulator may be further configured to regulate the switching output voltage to stay within a predefined range from the target output voltage using the current from another converter output line (e.g., S02) among the plurality of converter output lines.

[0085] At least one regulator may include or be a push-pull regulator and may include a switch (e.g., V O1 and V O2 See the transistor between. ). At least one of the plurality of regulators is configured to compare the switching output voltage with a predefined first threshold voltage (e.g., refer to the reference voltage connected to the negative (inverting) terminal of the comparator), and to control the switch coupled between the two converter output lines such that the switch is closed when the switching output voltage is lower than the predefined first threshold voltage and the switch is open when the switching output voltage is higher than the predefined first threshold voltage. A first comparator circuit (e.g., S O1 and S O2Refer to the comparator between it.) may be included.

[0086] FIG. 11 shows a SIMO circuit according to a further aspect of the present disclosure. According to this further aspect of the present disclosure, at least one of a plurality of voltage rails (V O1 ~V O4 ) may include a set of parallel push-pull regulators 1108. As represented herein, the pair of parallel push-pull regulators may include at least one amplifier pair configured as a high-side amplifier and a low-side amplifier. The positive terminal of the low-side amplifier may be connected to a low reference voltage, and the negative terminal of the high-side amplifier may be connected to a high reference voltage. The amplifiers may each be configured to activate a switch (shown on the right side of the amplifier. The output of the low-side amplifier opens and closes the connection between V O1 and V O2 , and the output of the high-side amplifier opens and closes the connection between V O2 and V O3 ). In this way, the output of the inductor during its dead phase is to the output rail (in this example, via switch S O2 to output rail V O2may be connected to (), and the voltage may be further changed via a parallel amplifier based on a predetermined low reference voltage and a predetermined high reference voltage. According to an aspect of the present disclosure, the low reference voltage and the high reference voltage may optionally be selected to be the same with only a small range between the high reference voltage and the low reference voltage. By doing so, the output of the parallel amplifier described herein is between the high reference voltage and the low reference voltage, and if the range between the reference voltages is small enough, the output may approximate the output of a linear regulator. The SIMO circuit may include at least one regulator configured to receive a switching output voltage and dynamically set the output voltage on one of a plurality of converter output lines. The at least one regulator may include a circuit configured to determine at least one of whether the switching output voltage exceeds a predefined upper threshold voltage greater than the target regulator output voltage or whether the switching output voltage is below a predefined lower threshold voltage less than the target regulator output voltage. The at least one regulator may be configured to use the current from another of the plurality of converter output lines to regulate the switching output voltage.

[0087] In various aspects of the present disclosure, a push-pull regulator may be provided between each pair of converter output rails having different potentials to control the output voltage of one of the converter output rails of the pair of converter output rails. Further, to control the output voltage of one of the converter output rails to be controlled, a first comparator may be provided to control a first switch coupled between the converter output rail to be controlled and a first adjacent (e.g., neighboring) converter output rail (carrying a higher voltage than the converter output rail to be controlled), and a second comparator may be provided to control a second switch coupled between the converter output line to be controlled and a second adjacent (e.g., neighboring) converter output rail (carrying a lower voltage than the converter output rail to be controlled).

[0088] FIG. 12 shows a method of operating a SIMO circuit described herein. The method includes: 1202 a plurality of switches supplying a switched output voltage at a converter output line of a plurality of converter output lines in response to an input voltage applied to an inductor; 1204 controlling the plurality of switches to control the switched output voltage; 1206 at least one regulator dynamically setting a regulator-specific predefined target output voltage associated therewith at an associated converter output line of the plurality of converter output lines, and regulating the switched output voltage to stay within a predefined range from the target regulator output voltage using current from another converter output line of the plurality of converter output lines. The SIMO circuit described herein may be configured according to a non-transitory computer-readable medium storing instructions that implement the above method of operating a single-inductor multiple-output circuit when executed by one or more processors.

[0089] FIG. 13 shows a method of operating a SIMO circuit described herein. The method includes: 1302 controlling a switching stage including an inductor and a plurality of switches to supply a switched output voltage at a converter output line of a plurality of converter output lines in response to an input voltage depending on the switching states of the plurality of switches; 1304 at least one regulator receiving the switched output voltage and dynamically setting an output voltage at a converter output line of the plurality of converter output lines, determining at least one of whether the switched output voltage exceeds a predefined upper threshold voltage greater than the target regulator output voltage or whether the switched output voltage is less than a predefined lower threshold voltage less than the target regulator output voltage, and regulating the switched output voltage using current from another converter output line of the plurality of converter output lines.

[0090] The SIMO circuit described in this specification may be configured according to a non - transitory computer - readable medium storing instructions that implement the above - described method of operating a single - inductor multiple - output circuit when executed by one or more processors.

[0091] The switch controller may control the switches in the SIMO converter 104 such that the inductor period occurs at a constant rate. The switch controller may control the switches in the SIMO converter 104 based on a constant switching frequency. Further, the switch controller may control the switches in the SIMO converter 104 such that the inductor period is discontinuous (e.g., the SIMO converter 104 operates according to the Discontinuous Conduction Mode (DCM)). A discontinuous inductor period may reduce or eliminate the influence of an inductor period on a subsequent inductor period.

[0092] FIG. 14 shows a graphical representation 1400 of a simulation of a separated inductor period (also referred to in the present disclosure as an inductor period, a separated inductor period, or a separated inductor switching period) according to at least one aspect described in the present disclosure. In FIG. 14, waveforms 1402a - d represent the current of the inductor during the inductor period. Waveforms 1402a - d show how the current of the inductor changes with time during the inductor period.

[0093] The inductor period may include a charging portion and a conducting portion. The charging portion is shown in FIG. 14 as portions 1410a - d, and the conducting portions are shown in FIG. 14 as portions 1412, 1414, 1416, 1418. For example, the charging portion of the first inductor period (waveform 1402a) includes portion 1410a, and the conducting portion of the first inductor period includes portion 1412.

[0094] The charging portions 1410a - d show an increase in the current of the inductor by charging the inductor using the input voltage as a positive voltage. The conducting portions 1412, 1414, 1416, 1418 disconnect the inductor from the input voltage and show a decrease in current by electrically coupling the inductor to an electrical device via the output portion of the SIMO system between the conducting portions 1412, 1414, 1416, 1418. For example, the conducting portions 1412, 1414, 1416, 1418 may correspond to electrically coupling the inductor to a first electrical device via a first output portion, to a second electrical device via a second output portion, to a third electrical device via a third output portion, or to a fourth electrical device via a fourth output portion, respectively. By electrically coupling a single electrical device to the inductor during each inductor cycle, the current of the inductor can decrease during the inductor cycle at a smooth or continuous rate.

[0095] FIG. 15 shows a graphical representation 1500 of a simulation in which an inductor is electrically coupled to a single electrical device during a separate inductor cycle, according to at least one aspect described in the present disclosure. In FIG. 15, waveforms 1524a - d represent the current of the inductor during the inductor cycle. Waveforms 1524a - d show how the current of the inductor changes over time during the inductor cycle. The charging portions are shown in FIG. 15 as portions 1510a - d, and the conducting portions are shown in FIG. 15 as portions 1512a, b and 1514a, b. For example, the charging portion of the first inductor cycle includes portion 1510a, and the conducting portion of the first inductor cycle includes portion 1512a.

[0096] The charging parts 1510a - d indicate an increase in the current of the inductor when the inductor is charged using the input voltage as a positive voltage. The conduction parts 1512a, b and 1514a, b indicate a decrease in the current of the inductor when the inductor is disconnected from the input voltage and electrically coupled to an electrical device via the output part of the SIMO converter between the conduction parts 1512a, b and 1514a, b. For example, the conduction parts 1512a, b may correspond to electrically coupling the inductor to a first electrical device via a first output part, and the conduction parts 1514a, b may correspond to electrically coupling the inductor to a second electrical device via a second output part.

[0097] Curves 1520 and 1522 show how the switching output voltage changes when the inductor is charged or conducting during the inductor period. Curve 1520 corresponds to the voltage level of the switching output voltage at the first output part, and curve 1522 corresponds to the voltage level of the switching output voltage at the second output part. As shown in FIG. 15, the voltage level of the switching output voltage at the first output part (e.g., curve 1520) and the voltage level of the switching output voltage at the second output part (e.g., curve 1522) increase between the corresponding conduction parts 1512a, b and 1514a, b. For example, the voltage level of the switching output voltage at the first output part (e.g., curve 1520) increases between the conduction parts 1512a, b, and the voltage level of the switching output voltage at the second output part (e.g., curve 1522) increases between the conduction parts 1514a, b.

[0098] When the current of the inductor reaches approximately zero amperes or the corresponding inductor period ends (e.g., the switch moves so that the subsequent charging portion occurs), the voltage level of the switching output voltage at the corresponding output portion begins to decrease. The voltage level of the switching output voltage can gradually decrease when the current reaches approximately zero amperes or the corresponding inductor period ends, due to the holding voltage of the second capacitor. For example, as shown in FIG. 15, when the conduction portion 1512a ends, the voltage level of the switching output voltage of the first output portion begins to decrease (e.g., the curve 1520 drops). As another example, as shown in FIG. 15, when the conduction portion 1514a ends, the voltage level of the switching output voltage of the second output portion begins to decrease (e.g., the curve 1522 drops).

[0099] FIG. 16 shows a graphical representation 1600 of a simulation in which an inductor is electrically coupled to two electrical devices during separate inductor periods, according to at least one aspect described in the present disclosure. In FIG. 16, waveforms 1526a - d represent the current of the inductor during the inductor period. Waveforms 1526a - d show how the current of the inductor changes over time during the inductor period. The charging portions are shown in FIG. 16 as portions 1510a - d, and the conduction portions are shown in FIG. 16 as portions 1512a - d and 1514a - d. For example, the charging portion of the first inductor period includes portion 1510a, and the conduction portions include portions 1512a and 1514a.

[0100] The conduction portions indicate a decrease in the current of the inductor by disconnecting the inductor from the input voltage and electrically coupling it to the electrical devices through two output portions of the SIMO converter between the conduction portions 1512a - d and 1514a - d. For example, the conduction portions 1512a - d may correspond to electrically coupling the inductor to the first electrical device through the first output portion, and the conduction portions 1514a - d may correspond to electrically coupling the inductor to the second electrical device through the second output portion.

[0101] As shown in FIG. 16, the voltage levels of the switching output voltages of the first output unit (e.g., curve 1520) and the second output unit (e.g., curve 1522) increase between the corresponding conduction portions 1512a to 1512d and 1514a to 1514d. For example, the voltage level of the switching output voltage of the first output unit (e.g., curve 1520) increases between the conduction portions 1512a to 1512d, and the voltage level of the switching output voltage of the second output unit (e.g., curve 1522) increases between the conduction portions 1514a to 1514d.

[0102] As shown in FIG. 16, each inductor period may include conduction portions corresponding to different electrical devices being electrically coupled to the inductor. For example, the inductor period may include charging portions 1510a to 1510d, followed by conduction portions 1512a to 1512d, and then conduction portions 1514a to 1514d. By electrically coupling a plurality of electrical devices to the inductor during each inductor period, the current of the inductor may decrease at a non-uniform or discontinuous rate. For example, the current of the inductor may decrease at a first rate between the conduction portions 1512a to 1512d and at a second rate between the conduction portions 1514a to 1514d.

[0103] As shown in FIGS. 15 and 16, the amount between the voltage levels when the peaks of the first voltage and the second voltage appear (ΔV with respect to curves 1520 and 1522 in FIGS. 15 and 16) O1 and ΔV O2 as shown. ) is greater for electrically coupling the inductor to a plurality of electrical devices for each inductor period (illustrated in FIG. 16) than for electrically coupling the inductor to a single electrical device for each inductor period (illustrated in FIG. 15). Further, as shown in FIGS. 15 and 16, the voltage ripple of the switching output voltage at the output unit increases for electrically coupling the inductor to a plurality of electrical devices for each inductor period compared to the case of electrically coupling the inductor to a single electrical device for each inductor period.

[0104] Examples of the switching time points at the start of the inductor period are T SW and 2TSW as shown in FIGS. 15 and 16. Although additional switching points may occur, they are not shown in FIG. 15 (for example, the switching points in the first inductor period and the fourth inductor period).

[0105] In some aspects of the present disclosure, the switching frequency of the inductor switching period can vary based on the inductance rating of inductor 202, the switching output voltage, or some combination thereof. In these and other aspects of the present disclosure, when the inductance rating of inductor 202 is between 1 nanohenry (nH) and 10 microhenries (μH), the switch controller may set the switching frequency between 1 kHz and 500 MHz. For example, the switching frequency may be set to 1 kHz when the switching output voltage is supplied to an electronic device including lower load conditions. As another example, the switching output frequency may be set between 100 and 500 MHz when the switching output voltage is supplied to an electronic device including higher load conditions. The decay phase of the inductor period (e.g., T on ) may include a range of times that can be any value less than the maximum value at the boundary of continuous conduction mode (CCM) or DCM operation. Table I shows examples of switching frequencies and Ton ranges for the energization phase. [Table 2]

[0106] FIG. 17 represents a flowchart of an exemplary method 1700 for operating a SIMO circuit in accordance with at least one aspect described in the present disclosure. Method 1700 may include one or more blocks 1702, 1704, 1706, or 1708. Although shown as separate blocks, the operations associated with one or more of the blocks of method 1700 may, depending on the particular implementation, be further divided into additional blocks, combined into fewer blocks, or removed.

[0107] In block 1702, the switching stage may be controlled. In some aspects of the present disclosure, the switching stage may include an inductor and a plurality of switches. In these and other aspects of the present disclosure, the switches and the inductor may supply a switching output voltage. Additionally, or alternatively, the switching output voltage may be supplied in response to an input voltage applied to the inductor. The switch may include a first switch coupled between a first terminal of the inductor and the input voltage. The switch may also include a second switch coupled between the first terminal of the inductor and a reference potential. Further, the switch may include a third switch coupled between a second terminal of the inductor and the reference potential.

[0108] In block 1704, the method may include operating the circuit in discontinuous conduction mode. Discontinuous conduction mode (DCM) may cause the current in the inductor to be made substantially equal to zero amperes before a subsequent inductor period occurs.

[0109] In block 1706, the method may include controlling the switch. In some aspects of the present disclosure, the method may include controlling the switch to supply the switching output voltage to different outputs in an inductor switching period separated from the switching output voltage. In these and other aspects of the present disclosure, the method may include controlling the switch to supply the switching output voltage to one electrical device for each separated inductor switching period.

[0110] In block 1708, the method may include switching between separated inductor switching periods. In some aspects of the present disclosure, the method may include switching between separated inductor switching periods at a constant switching frequency.

[0111] Modifications, additions, or omissions may be made to method 1700 without departing from the scope of the present disclosure. For example, the operations of method 1700 may be performed in a different order. Additionally, or alternatively, two or more operations may be executed simultaneously. Further, the operations and actions described are provided as examples by way of illustration, and some of the operations and actions may be optional, combined into fewer operations and actions, or extended into additional operations and actions without departing from the essence of the described embodiments.

[0112] Electrically coupling an inductor to a plurality of electrical devices every inductor cycle can increase the complexity and difficulty of tracking the state and settings of the voltage levels supplied to each electrical device. Further, electrically coupling an inductor to a plurality of electrical devices every inductor cycle can increase the amount of time it takes for the output voltage or the inductor current to recover. For example, if during one inductor cycle, the power level of a first output transitions from 0.5 watts (W) to 1 W and the power level of a second output transitions from 1 W to 0.5 W, this can keep the total current at the output constant until the first voltage level or the second voltage level drops even further. Keeping the total current at the output constant can make it take longer for the output voltage or the inductor current to recover.

[0113] Furthermore, electrically coupling an inductor to a plurality of electrical devices every inductor cycle can increase the complexity of a SIMO system compared to a SIMO system where the inductor is electrically coupled to one electrical device every inductor cycle. Further, electrically coupling an inductor to a plurality of devices during one inductor cycle can cause cross-regulation that releases the current stored in the inductor. For example, the output voltage level can change due to a change in the load on the inductor (e.g., the load caused by an electrical device being electrically coupled).

[0114] According to at least one aspect of the present disclosure, the switch can be controlled such that the switching output voltage is supplied to the electrical device via a single output of the SIMO system for each separated switching period. In some aspects of the present disclosure, the switch or inductor may operate in discontinuous conduction mode (DCM) to produce separated inductor periods. The operation of the switch or inductor in DCM can produce a period during which the current in the inductor is approximately zero amperes before the charging portion of the subsequent inductor period occurs.

[0115] The method may include controlling the switch and inductor such that a single electrical device is electrically coupled to the inductor for each inductor period (e.g., the inductor periods can be separated). In some aspects of the present disclosure, separating the induction periods can include producing a period during which the current in the inductor is approximately zero amperes before the charging portion of the subsequent inductor period begins. Each separated inductor period can include a charging portion, a conducting portion, and a period during which the current in the inductor is approximately zero amperes. The method may include controlling the switch such that the inductor receives the input voltage (e.g., during the charging portion), or electrically coupling the inductor to the electrical device and conducting via the output of the SIMO converter (e.g., during the conducting portion, or during the period when the current in the inductor is approximately zero amperes).

[0116] The operation of the inductor in DCM can reduce or eliminate the effects caused by one inductor period on other inductor periods. In some aspects of the present disclosure, the effects caused by one inductor period on other inductor periods may be due to the electrical device receiving the switching output voltage during the inductor period. For example, the operation of the inductor in DCM can reduce or eliminate the effects caused by a first electrical device on a second inductor period by the first electrical device receiving the switching output voltage during the first inductor period.

[0117] An inductor period can occur such that a switching output voltage is supplied to an electrical device via a separate output of the SIMO system during each inductor period. Some aspects of the present disclosure can supply a switching output voltage to only one electrical device via an output during a separate inductor period. For example, the method can include controlling a switch to supply a switching output voltage to a first electrical device via a first output of the SIMO system during a first separate inductor period and to supply a switching output voltage to a second electrical device via a second output of the SIMO system during a second separate inductor period. In some aspects of the present disclosure, the second separate inductor period can occur subsequent to the first separate inductor period.

[0118] In some aspects of the present disclosure, the separate inductor periods can occur at a constant switching frequency. In these and other aspects of the present disclosure, the constant switching frequency can cause the switch to transition between an open state and a closed state at a constant rate so as to supply either an input voltage to the inductor or a switching output voltage to an electrical device via one of the outputs of the SIMO converter. In these and other aspects of the present disclosure, the constant switching frequency can be within a frequency range from about 1 kHz to about 500 MHz.

[0119] In some aspects of the present disclosure, each separate inductor period can include a substantially similar duration. For example, the first separate inductor period can include a duration that is substantially similar to that of the second separate inductor period. In some aspects of the present disclosure, the separate inductor periods can include a duration in a time range from about 2 ns to about 1 ms. The duration of a separate inductor period can be based on the amount of time the switch is in a particular state (e.g., position).

[0120] In some aspects of the present disclosure, the first electrical device, the second electrical device, the third electrical device, or the fourth electrical device may include an electrical device located within a single circuit. In other aspects of the present disclosure, the first electrical device, the second electrical device, the third electrical device, or the fourth electrical device may include an electrical device located within two or more circuits.

[0121] In some aspects of the present disclosure, the peak current in the inductor during each induction period may be the same. In other aspects of the present disclosure, the peak currents in the inductor during two or more induction periods may be different.

[0122] In some aspects of the present disclosure, the switching frequency for controlling the switch may make the switching noise spur predictable (e.g., controllable). The predictability of the switching noise spur may enable the SIMO system to be designed to take into account the switching noise spur. Designing the SIMO system to take into account the switching noise spur may reduce or eliminate interference caused by the switching noise spur.

[0123] Supplying the switching output voltage to a single electrical device for each inductor period can enable the loads by each electrical device to be treated separately. Treating the loads by each electrical device separately can enable the conduction by the inductor to the electrical device to occur faster compared to a system that supplies the switching output voltage to a plurality of electrical devices for each inductor period. For example, treating the loads by each electrical device separately can enable the peak current for each electrical device to be controlled to be different for each electrical device. As another example, treating the loads by each electrical device separately can enable the cross-regulation of the current of the inductor for each inductor period to be reduced by supplying the switching output voltage to a single electrical device for each inductor period. As another example, treating the loads by each electrical device separately can reduce the complexity of the SIMO system with respect to a SIMO system that supplies the switching output voltage to a plurality of electrical devices for each inductor period.

[0124] The SIMO converter 104 and the LDO 106 can cooperate to supply the switching output voltage at the converter output. In some aspects of the present disclosure, the LDO 106 may implement a feedforward technique for regulating the switching output voltage, the operation of the LDO 106, or some combination thereof. The LDO may supply a voltage, a current, or some combination thereof in the forward direction to increase or decrease the duty cycle of the switches within the SIMO converter 104.

[0125] As described above, the voltage of the reset phase of inductor 202 can be applied to one or more of the output rails using one or more switches 204a. In this way, the voltages applied to the various output rails can be independent of each other or rail-specific. That is, the magnitude of the voltage applied to one or more output rails can depend at least in part on the portion of the reset phase during which one or more switches 204a are closed. By selecting switches to correspond to different periods of the reset phase, the various output rail voltages can be independently controlled, thereby enabling, for example, the first output rail to receive a first voltage and the second output rail to receive a second voltage different from the first voltage. A plurality of switches 204a may be closed simultaneously or in unison, thereby supplying the same voltage (based on the parallel connection to inductor 202) to the corresponding output rails simultaneously or in unison.

[0126] In accordance with aspects of the present disclosure, an LDO regulator can regulate a switching output voltage using a feedforward technique. The LDO can control a switch in a SIMO converter to supply a voltage, current, or some combination thereof in a forward direction to supply a switching output voltage within the voltage domain of an electrical device coupled to the converter output.

[0127] As described herein, a regulator may be utilized to regulate a voltage or current received from a discharge cycle of an inductor. These regulators may employ rapid transitions to keep the output voltage or current within a predefined range. A regulator, as described herein, is very effective at regulating the output voltage or current, but rapid regulator switching may exhibit a certain decrease in efficiency. In accordance with aspects of the present disclosure, as described herein, at least in relation to FIGS. 18 through 23, the operation of a regulator may be understood by detecting an equalization current that is added to or shunted from an output rail. The detected total equalization current (e.g., the difference between the added equalization current and the shunted current) is used with the modified output rail current such that the duty cycle of the inductor may be changed to approach the desired regulated voltage or regulated current, thereby reducing the transitions of the regulator and significantly improving efficiency.

[0128] FIG. 18 shows a block diagram of an exemplary system 1800 that includes a SIMO converter 104 and an LDO 106, in accordance with at least one aspect described in the present disclosure. System 1800 may also include a switch controller 1802. SIMO converter 104 may correspond to SIMO converter 104 described above in relation to FIG. 4. Further, LDO 106 may correspond to regulator 302a described above in relation to FIG. 4.

[0129] In FIG. 18, for purposes of brevity of illustration and discussion, only one LDO 106 and one switch controller 1802 are shown and discussed. In some aspects of the present disclosure, system 1800 may include only one LDO 106 and one switch controller 1802 as shown in FIG. 18. In other aspects of the present disclosure, system 1800 may include multiple LDOs 106 and multiple switch controllers 1802 or one switch controller 1802.

[0130] In some aspects of the present disclosure, LDO 106 may be electrically coupled to different output portions of SIMO converter 104. For example, system 1800 may include two LDOs 106 that are electrically coupled to different output portions of SIMO converter 104 as described elsewhere herein. Further, in these and other aspects of the present disclosure, switch controllers 1802 may each be electrically coupled to different LDOs 106. Alternatively, a single switch controller 1802 may be electrically coupled to the output of LDO 106.

[0131] In some aspects of the present disclosure, system 1800 may operate as a feedforward system. In these and other aspects of the present disclosure, system 1800 may supply a current or voltage representative of a current or voltage within LDO 106 to switch controller 1802. Switch controller 1802 may use the feedforwarded current or voltage to control the duty cycle of switches 204, 206, 208, or 210 within SIMO converter 104. In some aspects of the present disclosure, various elements shown within LDO 106 may be located within switch controller 1802. In these and other aspects of the present disclosure, functions described as being performed by LDO 106 or components within LDO 106 may be performed by switch controller 1802 or components within switch controller 1802.

[0132] LDO 106 may include an amplifier 1814 electrically coupled to the output portion of SIMO converter 104, a sixth switch 408, and a seventh switch 410. Amplifier 1814 may receive a switching output voltage 108 and a reference voltage. In some aspects of the present disclosure, first regulator terminal 1804 may be electrically coupled to input terminal 102. Amplifier 1814 may receive the reference voltage via terminal 1826. In some aspects of the present disclosure, amplifier 1814 may generate a regulator-specific target output voltage (e.g., a compensated output voltage) based on the switching output voltage and the reference voltage.

[0133] In some aspects of the present disclosure, LDO106 may include a Proportional Integration (PI) regulator 1808. In these and other aspects of the present disclosure, the PI regulator 1808 may include a proportional part (not shown) and an integral part (not shown). In some aspects of the present disclosure, the PI regulator 1808 may regulate the regulator-specific target output voltage of LDO106 to provide a regulated target output voltage 1830. The PI regulator 1808 may perform various functions on the regulator-specific target output voltage 1828b to generate the regulated target output voltage 1830. In some aspects of the present disclosure, the PI regulator 1808 may generate a regulator-specific target output current 1828a based on various functions performed on the regulator-specific target output voltage 1828b.

[0134] The switch controller 1802 may include an adder 1812. The adder 1812 may be electrically coupled to a sensor positioned by the first regulator terminal 1804, an output of the PI regulator 1808, and a sensor positioned by the second regulator terminal 1806. In some aspects of the present disclosure, the adder 1812 may add the target output voltage 1830 to at least one of a first voltage 1824 generated by a sensor at the first regulator terminal 1804 based on the current at the first regulator terminal 1804 and a second voltage 1820 generated by a sensor at the second regulator terminal 1806 based on the current at the second regulator terminal 1806. The adder 1812 may supply a total voltage 1834 based on the addition. In some aspects of the present disclosure, the adder 1812 may add the regulator-specific target output current 1828a to at least one of the current generated by a sensor at the first regulator terminal 1804 based on the current at the first regulator terminal 1804 and the current generated by a sensor at the second regulator terminal 1806 based on the current at the second regulator terminal 1806. The adder 1812 may supply a total current based on the addition.

[0135] The switch controller 1802 may also include a comparator circuit 1816 that is electrically coupled to a sensor positioned by the output of the adder 1812 and the first terminal of the inductor 202. In some aspects of the present disclosure, the comparator circuit 1816 may receive a total voltage 1834 and a voltage 1832 generated by the sensor based on the current at the first terminal of the inductor 202. The comparator circuit 1816 may compare the voltage 1832 based on the current detected at the first terminal with the total voltage 1834. Further, the comparator circuit 1816 may generate a comparison voltage 1836 based on the comparison. In other aspects of the present disclosure, the comparator circuit 1816 may receive a total current and a current generated by the sensor based on the current at the first terminal of the inductor 202. The comparator circuit 1816 may compare the current generated based on the current detected at the first terminal with the total current. Further, the comparator circuit 1816 may generate a comparison voltage 1836 based on the comparison.

[0136] The switch controller 1802 may further include a set reset (SR) latch circuit 1818 that is electrically coupled to the output of the comparator circuit 1816. In some aspects of the present disclosure, the output of the SR latch circuit 1818 may be electrically coupled to one or more of the switches 204, 206, 208, or 210 within the SIMO converter 104. The SR latch circuit 1818 may receive the comparison voltage 1836 and the clock signal 1840. The SR latch circuit 1818 may generate a duty cycle voltage 1838 based on the comparison voltage 1836 and the clock signal 1840.

[0137] In some aspects of the present disclosure, SIMO may include a switch (e.g., the fifth switch) (not shown) that is electrically coupled between the second terminal of the inductor and the input voltage. In these and other aspects of the present disclosure, the regulator may include a capacitor (e.g., the second capacitor) that is electrically coupled between the switching output voltage and the reference potential. The capacitor may include a capacitance in the range of about 1 nF to 10 μF.

[0138] FIG. 19 shows a graphical representation 1900 of the cross-regulation of a SIMO system with respect to the number of outputs to which an inductor is electrically coupled per inductor period, according to at least one aspect described in the present disclosure. For simulation, the SIMO system was electrically coupled between two and six electrical devices per inductor period. As shown in FIG. 19, the cross-regulation can vary based on the number of outputs to which the inductor is electrically coupled per inductor period.

[0139] FIG. 20 shows a flowchart of an exemplary method 2000 for operating a single inductor multiple output circuit, according to at least one aspect described in the present disclosure. Method 2000 may include one or more blocks 2002, 2004, 2006, 2008, or 2010. Although shown as separate blocks, the operations associated with one or more of the blocks of method 2000 may be divided into additional blocks, combined into fewer blocks, or omitted, depending on the particular implementation.

[0140] In block 2002, the method may include controlling a switch. In some aspects of the present disclosure, the switch may supply a switched output voltage in response to an input current supplied to the inductor. The method may include controlling the switch to control the switched output voltage.

[0141] In block 2004, the method may include dynamically setting a regulator-specific target output voltage associated with each. In some aspects of the present disclosure, an LDO may dynamically set a regulator-specific target output voltage associated with each.

[0142] In block 2006, the method may include regulating the switched output voltage. In some aspects of the present disclosure, the method may include regulating the switched output voltage using the input current. In these and other aspects of the present disclosure, the input current may flow through an LDO from a first regulator terminal to a second regulator terminal.

[0143] In block 2008, at least one of the first voltage or the second voltage may be determined. In some aspects of the present disclosure, the method may include determining a first voltage at a first regulator terminal and determining a second voltage at a second regulator terminal.

[0144] In block 2010, the method may include using at least one of the first voltage or the second voltage. In some aspects of the present disclosure, the method may include using the first voltage or the second voltage to control a switch.

[0145] Modifications, additions, or omissions may be made to method 2000 without departing from the scope of the present disclosure. For example, the operations of method 2000 may be performed in a different order. Additionally, or alternatively, two or more operations may be performed simultaneously. Further, the operations and actions described are given by way of example, and some of the operations and actions may be optional, may be combined into fewer operations and actions, or may be extended to additional operations and actions without departing from the essence of the described aspects.

[0146] FIG. 21 shows another block diagram of an exemplary operating circuit 2100 for operating a SIMO converter 104 in accordance with at least one aspect described in the present disclosure. Circuit 2100 may include a SIMO converter 104, an LDO 106, an electronic device 2101, an on-time adjustment loop 2105, a switch controller 2107, and a level shifter 2109.

[0147] For purposes of illustration and brevity of discussion, only one LDO 106 and one switch controller 2107 are shown and discussed in FIG. 21. In some aspects of the present disclosure, circuit 2100 may include only one LDO 106 and one switch controller 2107 as shown in FIG. 21. In other aspects of the present disclosure, circuit 2100 may include a plurality of LDOs 106 and a plurality of switch controllers 2107 or one switch controller 2107.

[0148] The SIMO converter 104 may correspond to the SIMO circuit 104 described elsewhere in the present disclosure. The LDO 106 may correspond to the LDO 106 described elsewhere in the present disclosure. In some aspects of the present disclosure, the SIMO converter 104 may include multiple output parts to supply the switching output voltage 108 at different values at the converter output part. In some aspects of the present disclosure, the electronic device 2101 may be electrically coupled to the converter output part. The SIMO converter 104 and the LDO 106 may operate to supply the switching output voltage 108 to the electronic device 2101.

[0149] In some aspects of the present disclosure, the on-time adjustment loop 2105 may include some or all of the LDO 106 in FIG. 18. In these and other aspects of the present disclosure, the on-time adjustment loop 2105 may include some or all of the switch controller 1802 in FIG. 18.

[0150] The on-time adjustment loop 2105 may receive the switching output voltage 108 and may also receive a reference voltage via terminal 1826. The on-time adjustment loop 2105 may compare the switching output voltage 108 with the reference voltage. The on-time adjustment loop 2105 may supply a duty cycle voltage 1838 (e.g., V TON ) based on the comparison between the switching output voltage 108 and the reference voltage.

[0151] The switch controller 2107 may be configured to control the switches within the SIMO converter 104. The switch controller 2107 may control the switches within the SIMO converter 104 to selectively apply the switching output voltage 108 to the converter output part.

[0152] The switch controller 2107 may generate one or more switching voltages 2111 based on the duty cycle voltage 1838 and the clock voltage 2103. In some aspects of the present disclosure, when the duty cycle voltage 1838 is logic high and the clock voltage 2103 is received, the switch controller 2107 may turn off the high-side switch (e.g., switch 206 in FIG. 2) in the SIMO converter 104 and turn on the low-side switch (e.g., switch 208 in FIG. 2) and the output switch (switch 204a in FIG. 2) in the SIMO converter 104, and may generate the switching voltage 2111.

[0153] In some aspects of the present disclosure, before controlling one or more switches to transition to the closed position (e.g., turn on), the switch controller 2107 may insert a dead time (t DEAD ) into the switching voltage 2111 so that shoot-through current does not occur in the SIMO converter 104.

[0154] The level shifter 2109 may receive the switching voltage 2111. The level shifter 2109 may shift one or more voltage levels of the switching voltage 2111 to a level sufficient to transition the corresponding switches in the SIMO converter 104 between the open position and the closed position. The level shifter 2109 may generate a gate voltage 2113 based on the switching voltage 2111. In some aspects of the present disclosure, the level shifter 2109 may delay the gate voltage 2113 based on the corresponding stage of the SIMO converter 104 that is to receive the gate voltage 2113.

[0155] The SIMO converter 104 may receive the gate voltage 2113 and may operate the switches implemented in the SIMO converter 104 accordingly.

[0156] In some aspects of the present disclosure, the on-time adjustment loop 2105, the switch controller 2107, the level shifter 2109, or some combination thereof may be optimized for efficiency.

[0157] FIG. 22 shows another block diagram of an exemplary operating environment or system 2200 for operating the SIMO converter 104 in accordance with at least one aspect described in the present disclosure. The environment 2200 may include a SIMO converter 104, an LDO 106, an on-time adjustment loop 2105, and a switch controller 2107.

[0158] The SIMO converter 104 may correspond to the SIMO converter 104 described above in connection with FIG. 4. Further, the LDO 106 may correspond to the regulator 302a described above in connection with FIG. 4.

[0159] In FIG. 22, for purposes of illustration and brevity of discussion, only one LDO 106 is shown and discussed. In some aspects of the present disclosure, the environment 2200 may include only one LDO 106 as shown in FIG. 22. In other aspects of the present disclosure, the environment 2200 may include multiple LDOs 106.

[0160] The LDO 106 may include a comparator 2215 that is electrically coupled to the output of the SIMO converter 104. The comparator 2215 may receive the switching output voltage 108. The comparator 2215 may receive a reference voltage via terminal 2217. The comparator 2215 may compare the reference voltage with the switching output voltage. In some aspects of the present disclosure, the comparator 2215 may control a sixth switch 2205 to regulate the switching output voltage based on the comparison.

[0161] The on-time adjustment loop 2105 (shown in FIG. 21.) may include an amplifier 1814. The amplifier 1814 may receive the switching output voltage 108. The amplifier 1814 may receive a reference voltage via terminal 1826. The amplifier 1814 may compare the reference voltage with the switching output voltage. In some aspects of the present disclosure, the amplifier 1814 may generate a regulator-specific target output voltage based on the comparison.

[0162] In some aspects of the present disclosure, the on-time adjustment loop 2105 may include a PI regulator 1808. The PI regulator 1808 may regulate the regulator-specific target output voltage 1828 (or current) of the LDO 106 to provide a regulated target output voltage 1830. The PI regulator 1808 may perform various functions on the regulator-specific target output voltage 1828 to generate a regulated target output voltage 1830 (or current).

[0163] The on-time adjustment loop 2105 may also include an adder 1812. The adder 1812 may be electrically coupled to a sensor positioned by the first regulator terminal 1804 and to the output of the PI regulator 1808. In some aspects of the present disclosure, the adder 1812 may add the target output voltage 1830 and a first voltage 1824 generated by a sensor at the first regulator terminal 1804 based on the current at the first regulator terminal 1804. The adder 1812 may provide a total voltage 1834 based on the addition. In some aspects of the present disclosure, the adder 1812 may perform the addition based on a current signal instead of a voltage signal as described above in connection with FIG. 18.

[0164] The on-time adjustment loop 2105 may also include a comparator 1816 electrically or operably coupled to the output of the adder 1812 and to the first terminal of the inductor 202. The comparator 1816 may receive the total voltage 1834 and the input voltage 1832. The comparator 1816 may compare the total voltage 1834 with the input voltage 1832 at the first terminal of the inductor 202. The comparator 1816 may generate a comparison voltage 1836 based on the comparison.

[0165] The switch controller 2107 may be configured to control the switches in the SIMO converter 104. The switch controller 2107 may control the switches in the SIMO converter 104 to selectively apply the switching output voltage 108 to the converter output.

[0166] The switch controller 2107 can generate one or more switching voltages 2111 based on a comparison voltage 1836 and a clock voltage 2103.

[0167] In some aspects of the present disclosure, the environment 2200 may also include a level shifter 2109 to generate a gate voltage 2113.

[0168] FIG. 23 shows another block diagram of an exemplary operating environment 2300 for operating the SIMO converter 104 in accordance with at least one aspect described in the present disclosure. The environment 2300 may include a SIMO converter 104, an LDO 106, an on-time adjustment loop 2105, and a switch controller 2107.

[0169] The SIMO converter 104 may correspond to the SIMO converter 104 described above in connection with FIG. 4. Further, the LDO 106 may correspond to the LDO 106 described above in connection with FIG. 4.

[0170] In FIG. 23, for the sake of brevity of illustration and discussion, only one LDO 106 is illustrated and discussed. In some aspects of the present disclosure, the environment 2300 may include only one LDO 106 as shown in FIG. 23. In other aspects of the present disclosure, the environment 2300 may include multiple LDOs 106.

[0171] In some aspects of the present disclosure, LDO106 may include a digital linear regulator. LDO106 may include a digital gate controller 2319. The digital gate controller 2319 may be electrically coupled to the converter output. The digital gate controller 2319 may generate a gate control signal. The digital gate controller 2319 may generate a gate control signal to control the gate of the switch 621 within LDO106 to regulate the switching output voltage 108. The digital gate controller 2319 may generate a gate control signal based on the difference between the switching output voltage 108 and the reference signal 2323. The digital gate controller 2319 may generate the gate control signal as a digital signal. Each gate control signal may correspond to a different switch within the switch 621. For example, the first gate control signal may control the gate of the first switch within the switch 621, and the second gate control signal may control the gate of the second switch within the switch 621.

[0172] The digital gate controller 2319 may generate a specific number of the gate control signals as logic high based on the difference between the switching output voltage 108 and the reference signal 2323. As the difference between the switching output voltage 108 and the reference signal 2323 changes, the digital gate controller 2319 may generate more or fewer of the gate control signals as logic high. For example, as the difference decreases, the digital gate controller 2319 may reduce the number of gate control signals that are logic high.

[0173] Switch 621 can regulate the switching output voltage by increasing the current level of the switching output voltage. Switch 621 can receive an input signal (e.g., an input voltage) and supply the input signal to the converter output section at a controlled current level. Switch 621 can receive the input signal from input terminal 102. The controlled current level of the input signal supplied to the converter output section can be based on the number of switches within switch 621 that are in a closed state (e.g., based on the number of gate control signals that are at logic high). Each switch within switch 621 that is in a closed state can increase the current level of the input signal supplied to the converter output section. For example, when all of switch 621 is in a closed state, switch 621 can supply the input signal at a high current level. As another example, when one of the switches of switch 621 is in a closed state, switch 621 can supply the input signal at a current level lower than the high current level (e.g., one-fourth of the high current level).

[0174] The on-time adjustment loop 2105 may include an amplifier 1814. Amplifier 1814 can receive the switching output voltage 108. Amplifier 1814 can receive a reference voltage via terminal 1826. Amplifier 1814 can compare the reference voltage with the switching output voltage. In some aspects of the present disclosure, amplifier 1814 can generate a regulator-specific target output voltage 1828 based on the comparison.

[0175] In some aspects of the present disclosure, the on-time adjustment loop 2105 may include a PI regulator 1808. The PI regulator 1808 can regulate the regulator-specific target output voltage 1828 (or current) to supply a regulated target output voltage 1830 (or current). The PI regulator 1808 may perform various functions with respect to the regulator-specific target output voltage 1828 to generate the regulator-specific target output voltage 1830 (or current).

[0176] The on-time adjustment loop 2105 may include a current source (hereinafter also referred to as "I source") array 2309. The I source array 2309 may be electrically coupled to the output of the digital gate controller 2319. Further, the I source array 2309 may be electrically coupled to the adder 1812. The I source array 2309 may receive a gate control signal from the digital gate controller 2319. The I source array 2309 may generate a first voltage 1824 (or current) based on the gate control signal. In some aspects of the present disclosure, the I source array 2309 may generate the first voltage 1824 (or current) based on the number of gate control signals that are logic high. For example, when all gate control signals are logic high (e.g., all switches in the switch 621 are in the closed state), the I source array 2309 may generate the first voltage 1824 (or current) at a high level. As another example, when two gate control signals are logic high (e.g., two switches in the switch 621 are in the closed state), the I source array 2309 may generate the first voltage 1824 (or current) at a partial high level (e.g., at half the high level). In some aspects of the present disclosure, the I source array 2309 may generate the first voltage 1824 as a copy of the current level in the SIMO buck-boost converter 104 (e.g., the current in the inductor 202).

[0177] The on-time adjustment loop 2105 may include an adder 1812. The adder 1812 may be electrically coupled to the outputs of the I source array 2309 and the PI regulator 1808. In some aspects of the present disclosure, the adder 1812 may add the target output voltage 1830 (or current) and the first voltage 1824 (or current) from the I source array 2309. The adder 1812 may supply a total voltage 1834 (or current) based on the addition.

[0178] The on-time adjustment loop 2105 may also include a comparator 1816 that is electrically coupled to the output of the adder 1812 and a sensor positioned by the first terminal of the inductor 202. The comparator 1816 may receive the total voltage 1834 (or current) and a voltage 1832 (or current) based on the current at the first terminal of the inductor 202. The comparator 1816 may compare the total voltage 1834 (or current) with the voltage 1832 (or current). The comparator 1816 may generate a comparison voltage 1836 (or current) based on the comparison.

[0179] The switch controller 2107 may be configured to control the switches in the SIMO converter 104. The switch controller 2107 may control the switches in the SIMO converter 104 to selectively apply the switching output voltage 108 to the converter output. The switch controller 2107 may generate one or more switching voltages 2111 based on the comparison voltage 1836 and the clock voltage 2103.

[0180] In some aspects of the present disclosure, the environment 2300 may also include a level shifter 2109 configured to generate the gate voltage 2113.

[0181] FIG. 24 shows another block diagram of an exemplary operating environment 2400 for operating the SIMO converter 104 in accordance with at least one aspect described in the present disclosure. The environment 2400 may include the SIMO converter 104, the LDO 106, the on-time adjustment loop 2105, and the switch controller 2107.

[0182] The SIMO converter 104 may correspond to the SIMO converter 104 described above in connection with FIG. 4. Further, the LDO 106 may correspond to the LDO 106 described above in connection with FIG. 4.

[0183] In FIG. 24, for the sake of brevity of illustration and discussion, only one LDO 106 is illustrated and discussed. In some aspects of the present disclosure, the environment 2400 may include only one LDO 106 as shown in FIG. 24. In other aspects of the present disclosure, the environment 2400 may include a plurality of LDOs 106.

[0184] In some aspects of the present disclosure, the LDO 106 may include a digital push-pull regulator. The LDO 106 may include a first digital gate controller 2319a and a second digital gate controller 2319b. The digital gate controllers 2319a-b may be electrically coupled to the converter output. The digital gate controllers 2319a-b may generate a gate control signal. The digital gate controllers 2319a-b may generate a gate control signal to control the gates of the switches 621a-b within the LDO 106 to regulate the switching output voltage 108.

[0185] The first digital gate controller 2319a may receive a low reference signal 2325 and the switching output voltage 108. The first digital gate controller 2319a may generate a corresponding gate control signal based on the switching output voltage 108 and the low reference signal 2325. In some aspects of the present disclosure, the first digital gate controller 2319a may control the switching output voltage to exceed a low threshold as described above in connection with FIG. 23.

[0186] The second digital gate controller 2319b may receive the high reference signal 2327 and the switching output voltage 108. The second digital gate controller 2319b may generate a corresponding gate control signal based on the switching output voltage 108 and the high reference signal 2327. In some aspects of the present disclosure, the second digital gate controller 2319b may control the switching output voltage to be below a high threshold. The second digital gate controller 2319b may operate in a manner similar to the digital gate controller 2319 of FIG. 23, but instead of regulating the current level of the switching output voltage to be above a threshold, the second digital gate controller 2319b may regulate the current level of the switching output voltage to be below a high threshold based on the gate control signal.

[0187] The on-time adjustment loop 2105 may include an amplifier 1814. The amplifier 1814 may receive the switching output voltage 108. The amplifier 1814 may receive a reference voltage via terminal 1826. The amplifier 1814 may compare the reference voltage with the switching output voltage. In some aspects of the present disclosure, the amplifier 1814 may generate a regulator-specific target output voltage 1828 based on the comparison.

[0188] In some aspects of the present disclosure, the on-time adjustment loop 2105 may include a PI regulator 1808. The PI regulator 1808 may regulate the regulator-specific target output voltage of the LDO 106 to supply a regulated target output voltage 1830 (or current). The PI regulator 1808 may perform various functions on the regulator-specific target output voltage 1828 to generate the regulator-specific target output voltage 1830 (or current). The LDO 106 of FIG. 24 may operate in a manner similar to that described for the digital push-pull regulator 702a in connection with FIG. 7.

[0189] The on-time adjustment loop 2105 may include a first I source array 2309a and a second I source array 2309b. The first I source array 2309a may be electrically coupled to the output of the first digital gate controller 2319a. The second I source array 2309b may be electrically coupled to the output of the second digital gate controller 2319b. Further, the I source arrays 2309a-b may be electrically coupled to the adder 1812. The I source arrays 2309a-b may receive corresponding gate control signals from the digital gate controllers 2319a-b. The first I source array 2309a may generate a first voltage 1824 (or current) based on the gate control signal from the first digital gate controller 2319a. In some aspects of the present disclosure, the first I source array 2309a may generate the first voltage 1824 (or current) based on the number of gate control signals received from the first digital gate controller 2319a that are logic high, as described above in connection with FIG. 23. The second I source array 2309b may generate a second voltage 1820 (or current) based on the gate control signal from the second digital gate controller 2319b. In some aspects of the present disclosure, the second I source array 2309b may generate the second voltage 1820 (or current) based on the number of gate control signals received from the second digital gate controller 2319b that are logic high, as described above in connection with FIG. 23.

[0190] The on-time adjustment loop 2105 may include an adder 1812. The adder 1812 may be electrically coupled to the outputs of the I source arrays 2309a-b and the PI regulator 1808. In some aspects of the present disclosure, the adder 1812 may add a target output voltage 1830 (or current), the first voltage 1824 (or current), the second voltage 1820 (or current), or some combination thereof. The adder 1812 may supply a total voltage 1834 (or current) based on the addition.

[0191] The on-time adjustment loop 2105 may also include a comparator 1816 that is electrically coupled to the output of the adder 1812 and a sensor positioned by the first terminal of the inductor 202. The comparator 1816 may receive the total voltage 1834 (or current) and the voltage 1832 (or current) based on the current at the first terminal of the inductor 202. The comparator 1816 may compare the total voltage 1834 (or current) with the voltage 1832 (or current). The comparator 1816 may generate a comparison voltage 1836 (or current) based on the comparison.

[0192] The switch controller 2107 may be configured to control the switches in the SIMO converter 104. The switch controller 2107 may control the switches in the SIMO converter 104 to selectively apply the switching output voltage 108 to the converter output. The switch controller 2107 may generate one or more switching voltages 2111 based on the comparison voltage 1836 and the clock voltage 2103.

[0193] In some aspects of the present disclosure, the environment 2400 may also include a level shifter 2109 to generate the gate voltage 2113.

[0194] A system including a SIMO converter, an LDO, and a switch controller may operate as a feedforward system. The feedforward system may feed forward (e.g., supply) a voltage, a current, or some combination thereof from the SIMO converter or the LDO to the switch controller. For example, a first voltage / current based on the current at the first regulator terminal and a second voltage / current based on the current at the second regulator terminal may be feedforwarded. The switch controller may use the feedforwarded voltage / current to control the duty cycle of the switches in the SIMO converter. In some aspects of the present disclosure, the switch controller or a combination of the switch controller and the LDO may be integrated with a tuning loop, such as an on-time adjustment loop.

[0195] With a hybrid SIMO LDO structure, the SIMO converter can provide higher efficiency performance for the LDO, and the LDO can improve transient performance. To improve the efficiency of the system, the operation of the LDO can be minimized, and the operation of the SIMO converter can be maximized. In some aspects of the present disclosure, to increase the operation of the SIMO converter, it may be implemented to increase (or increase) the duty cycle of the switches in the SIMO converter. The voltage fed forward from the SIMO converter and the switch controller increase the duty cycle of the switches.

[0196] The LDO may be configured to dynamically set the regulator-specific target output voltage associated with each. In some aspects of the present disclosure, the LDO may change the regulator-specific target output voltage associated with each based on operating factors within the SIMO converter or the LDO. For example, the LDO may regulate the switching output voltage to stay within a predefined range of the target output voltage. In these and other aspects of the present disclosure, the input current may flow through the LDO from the first regulator terminal to the second regulator terminal.

[0197] In some aspects of the present disclosure, the LDO may include a comparator (e.g., a third comparator) configured to compare the switching output voltage with a predefined third threshold voltage. In some aspects of the present disclosure, the predefined third threshold voltage may be programmed based on the steady-state voltage level of the switching output voltage. The comparator may generate a regulated target output voltage based on the comparison.

[0198] In some aspects of the present disclosure, for example, as shown in FIG. 18, the LDO may include a PI circuit including a proportional part and an integral part. The PI circuit, for example, a PI regulator, may receive a regulator-specific target output voltage from an amplifier. The PI regulator may perform a proportional function or an integral function with respect to the regulator-specific target output voltage. The PI may supply a regulated target output voltage based on the function performed with respect to the regulator-specific target output voltage. In some aspects of the present disclosure, only the proportional part of the PI circuit may perform a function with respect to the regulator-specific target output voltage. In other aspects of the present disclosure, only the integral part of the PI circuit may perform a function with respect to the regulator-specific target output voltage. Alternatively, both the proportional part and the integral part of the PI circuit may perform a function with respect to the regulator-specific target output voltage.

[0199] In some aspects of the present disclosure, the LDO or the switch controller may include an adder. The LDO or the switch controller may use a first voltage / current, a second voltage / current, or some combination thereof to control the switches in the SIMO converter. In some aspects of the present disclosure, the LDO may determine a first voltage / current based on the current at the first regulator terminal or a second voltage / current based on the current at the second regulator terminal. For example, the adder may receive a regulated target output voltage from the PI circuit, a first voltage / current from a sensor by the first regulator terminal, and / or a second voltage / current from a sensor by the first terminal of the inductor. The adder may sum the regulated target output voltage with the first voltage / current and / or the second voltage / current. The adder may generate a total voltage / current based on the sum of the regulated target output voltage and the first voltage / current and / or the second voltage / current.

[0200] According to some aspects of the present disclosure, the switch controller may include a comparator (e.g., the fourth comparator) configured to receive a total voltage and a voltage / current based on the current at the first terminal of the inductor. According to other aspects of the present disclosure, the comparator may be configured as a pre-stage of the switch controller. The comparator may compare a regulated target output voltage / current with a voltage / current based on the current at the first terminal of the inductor. The comparator may supply a comparison voltage based on the comparison.

[0201] The switch controller may include an SR latch circuit configured to receive the comparison voltage. The SR latch circuit may also receive a clock signal. In some aspects of the present disclosure, the comparison voltage may operate as a reset signal for the SR latch circuit. In these and other aspects of the present disclosure, the clock signal may operate as a set signal for the SR latch circuit. The SR latch circuit may generate a duty cycle voltage based on the clock signal and the comparison voltage (e.g., to control switches in a SIMO converter). The duty cycle voltage may control the duty cycle of one or more switches in the SIMO converter.

[0202] In some aspects of the present disclosure, when the clock signal goes high and the comparison voltage falls below the threshold level, the SR latch circuit can be set and can supply a duty cycle voltage. The fed-forward current may be added to the duty cycle control of the switches in the SIMO converter to increase (increase) the duty cycle of one or more switches in the SIMO converter. In some aspects of the present disclosure, increasing the duty cycle of one or more switches in the SIMO converter can increase the amount of time that one or more switches are in a closed position (e.g., a propagation position) or an open position (e.g., a non-propagation position). In some aspects of the present disclosure, when the comparison voltage exceeds the corresponding threshold level, the SR latch circuit can be reset, stop supplying the duty cycle voltage, and one or more switches in the SIMO converter can move to an open position (e.g., a non-propagation position). In these and other aspects of the present disclosure, when the comparison voltage exceeds the corresponding threshold level, the SR latch circuit can be reset, cannot supply the duty cycle voltage, and one or more switches in the SIMO converter can operate according to a predefined duty cycle.

[0203] In some aspects of the present disclosure, compared to a system without a switch controller, the duty cycle voltage that controls one or more switches can increase the duty cycle of one or more switches in the SIMO converter and can increase the rate at which the inductor is charged. In some aspects of the present disclosure, the switch controller can increase (e.g., increase) the duty cycle of one or more switches in the SIMO converter when the total voltage increases. In these and other aspects of the present disclosure, the switch controller can reduce (e.g., decrease) the duty cycle of one or more switches in the SIMO converter when the total voltage supplied by the associated regulator decreases. By controlling the duty cycle of one or more switches in the SIMO converter, the switch controller can control the switching output voltage.

[0204] An LDO and a switch controller (e.g., a comparator, a PI circuit, an adder, or an SR latch circuit) may be used to detect whether the output of the SIMO is to be increased, decreased, or maintained. In some aspects of the present disclosure, the LDO and the switch controller may be implemented as an on-time adjustment loop. In the on-time adjustment loop, the duty cycle of one or more switches in the SIMO converter, the amount of time that the duty cycle is on (e.g., T on ) can be increased or decreased to change the rate at which the inductor is charged or the rate at which the current on the inductor is dissipated. One or more aspects described in the present disclosure may detect an increase in current in an LDO that can increase the amount of time (e.g., T on ) that the duty cycle voltage is supplied. Also, the current of the LDO may decrease with an increase in the amount of time that the duty cycle voltage is supplied.

[0205] In some aspects, further optimization of the system can be obtained using a trigger of the power train or other optimization methods.

[0206] One or more of the aspects described in the present disclosure can increase the duty cycle of one or more switches in the SIMO faster than a SIMO system that does not include an LDO or a feedforward controller. Further, one or more of the aspects described in the present disclosure increase the rate at which the inductor is charged or the rate at which the stored current is dissipated. Further, one or more of the aspects described in the present disclosure reduce the circuit complexity of the SIMO system.

[0207] In some aspects of the present disclosure, the LDO, the on-time adjustment loop, the switch controller, or some combination thereof may include a sense field effect transistor (SenseFET). The SenseFET can detect (e.g., sense) one or more voltages in the SIMO converter (e.g., the switching output voltage). In some aspects of the present disclosure, the gate-source voltage (V gs ) and the gate-drain voltage (V gd) may be the same as or similar to one or more voltages within the SIMO converter. The SenseFET may direct a portion of the current within the SIMO converter to control one or more voltages within an LDO, an on-time adjustment loop, a switch controller, or some combination thereof.

[0208] In some aspects of the present disclosure, the SenseFET may include an N:1 size ratio to the SIMO converter. In these and other aspects of the present disclosure, the SenseFET may direct the current within the SIMO converter at a 1 / N ratio to control one or more voltages within an LDO, an on-time adjustment loop, a switch controller, or some combination thereof.

[0209] In some aspects of the present disclosure, an LDO, an on-time adjustment loop, a switch controller, or some combination thereof may include an instrumentation amplifier. An LDO, an on-time adjustment loop, a switch controller, or some combination thereof may detect a voltage drop in the SIMO converter. The instrumentation amplifier may be configured to amplify the voltage drop in the SIMO converter. The instrumentation amplifier may increase the voltage drop in the SIMO converter to control one or more voltages within an LDO, an on-time adjustment loop, a switch controller, or some combination thereof.

[0210] In some aspects of the present disclosure, the LDO may include a digital LDO. The LDO may include a digital gate controller and an I-source array. The LDO may detect the current in the SIMO converter based on the number of active switches (e.g., switches in a closed state). The LDO may include switches that are electrically coupled between the input part of the SIMO converter and the converter output part. The digital gate controller may control the switches together with the LDO. The digital gate controller may transition the switches within the LDO between an open position and a closed position based on the switching output voltage and a reference voltage. The I-source array may detect the current at the digital gate controller output. The on-time adjustment loop may adjust the total voltage based on the detected current at the output of the digital gate controller.

[0211] The electronic device electrically coupled to the converter output part may include different settings for the voltage ripple of the switching output voltage. In some aspects of the present disclosure, the switch controller may control the switches in the SIMO converter 104 to supply the switching output voltage to the electronic device including sensitive voltage ripple settings more frequently. The switch controller that supplies the switching output voltage to these electronic devices more frequently can reduce the voltage ripple of the switching output voltage at the corresponding converter output part.

[0212] According to aspects of the present disclosure, the switch controller may control the ripple of the switching output voltage by controlling the switches in the SIMO converter. Electrical components may have various tolerance ranges for voltage ripple. Some components can be very robust against ripple and can withstand a significant voltage ripple, while other components are relatively sensitive to ripple and require significant voltage control to protect the components and ensure proper operation. For example, a USB port ideally operates at 5V, but some USB-connected devices may have sufficient ripple tolerance to function well within a voltage range (e.g., a virtual range of 4.45V to 5.25V). However, other USB-connected devices may require a voltage much closer to 5V constant. The magnitude of the ripple can be determined, in part, by controlling switches 204a - n.

[0213] FIG. 25 shows a block diagram of an exemplary system 2500 including a SIMO 104, according to at least one aspect described in the present disclosure. System 2500 may also include a master controller 2502 and a switch controller 2504. SIMO 104 may correspond to the SIMO 104 described above in relation to FIG. 4.

[0214] In FIG. 25, for the sake of brevity of illustration and discussion, only one master controller 2502 and one switch controller 2504 are shown and discussed. In some aspects of the present disclosure, system 2500 may include only one master controller 2502 and one switch controller 2504 as shown in FIG. 25. In other aspects of the present disclosure, system 2500 may include two or more master controllers 2502 and two or more switch controllers 2504.

[0215] In some aspects of the present disclosure, the master controller 2502 may be electrically coupled to different output portions of the SIMO 104. In these and other aspects of the present disclosure, the switch controller 2504 may be electrically coupled to the master controller 2502. Further, in some aspects of the present disclosure, the switch controller 2504 may be electrically coupled to one or more of the switches 204a - n within the SIMO 104 represented as a dashed rectangle in FIG. 25. The switch controller 2504 is shown in FIG. 25 as being coupled to the dashed rectangle rather than to each of the switches 204a - n for the sake of brevity of illustration.

[0216] In some aspects of the present disclosure, the system 2500 may operate to control the voltage ripple of the switching output voltages 108a - n supplied to an electrical device electrically coupled to the output portion of the SIMO 104. In these and other aspects of the present disclosure, the master controller 2502 may determine the switching output voltages 108a - n at one or more output portions. The switch controller 2504 may be configured to control the duty cycle of the switches 204a - n based on the signals supplied by the master controller 2502 based on the switching output voltages 108a - n.

[0217] FIG. 26 shows a graphical representation 2600 of a simulation in which an inductor is electrically coupled to two electrical devices during separate inductor cycles, according to at least one aspect described in the present disclosure. In FIG. 26, the waveforms 2606a - e represent the current in the inductor during the inductor cycle. The waveforms 2606a - e show how the current in the inductor changes over time during the inductor cycle. The charging portions of the inductor cycle are shown as portions 2608a - e in FIG. 26, and the discharging portions of the inductor cycle are shown as portions 2610, 2612, 2614, 2616, and 2618 in FIG. 26. For example, the charging portion of the first inductor cycle 2606a includes portion 2608a, and the discharging portion of the first inductor cycle 2606a includes portion 2610.

[0218] In some aspects of the present disclosure, an inductor may be electrically coupled to an electrical device between charging portions 2608a - e and discharging portions 2610, 2612, 2614, 2616, and 2618. In these and other aspects of the present disclosure, charging portions 2608a - e exhibit an increase in current in the inductor due to the inductor being charged as a positive voltage using the input voltage at a higher rate than the inductor is discharged. For example, charging portions 2608a - e may correspond to an inductor that receives an input voltage and is electrically coupled to a first electrical device via a first output portion. Discharging portions 2610, 2612, 2614, 2616, and 2618 exhibit a decrease in current in the inductor by disconnecting the inductor from the input voltage and electrically coupling the inductor to other electrical devices. For example, discharging portions 2610, 2612, 2614, 2616, and 2618 may correspond to electrically coupling the inductor to a second electrical device, a third electrical device, a fourth electrical device, a fifth electrical device, and a sixth electrical device, respectively. During each inductor cycle, the inductor is electrically coupled to the first electrical device during charging portions 2608a - e and to a different electrical device during discharging portions 2610, 2612, 2614, 2616, and 2618.

[0219] Curves 2620, 2622, 2624, 2626, and 2628 show how the switching output voltage at each output of the SIMO system changes by charging or discharging the inductor during the inductor cycle. Curve 2620 corresponds to the voltage level of the switching output voltage at the first output. Curve 2626 corresponds to the voltage level of the switching output voltage at the second output. Curve 2624 corresponds to the voltage level of the switching output voltage at the third output. Curve 2626 corresponds to the voltage level of the switching output voltage at the fourth output. Curve 2628 corresponds to the voltage level of the switching output voltage at the fifth output.

[0220] As shown in FIG. 26, the voltage level of the switching output voltage at the first output portion increases between the corresponding charging portions 2608a to e. Further, as shown in FIG. 26, the voltage levels of the switching output voltages at the second output portion, the third output portion, the fourth output portion, and the fifth output portion increase between the corresponding discharging portions 2610, 2612, 2614, 2616, and 2618. For example, the voltage level of the switching output voltage at the second output portion increases between the discharging portions 2610 and 2618 (e.g., curve 2622), and the voltage level of the switching output at the fourth output portion (e.g., curve 2626) increases between the discharging portion 2614.

[0221] When the current in the inductor reaches approximately zero amperes or the corresponding inductor period ends (e.g., the switch moves so that the subsequent charging portion occurs), the voltage level of the switching output voltage at the corresponding output portion begins to decrease. The voltage levels of the switching output voltages at different output portions can gradually decrease when the current reaches approximately zero amperes or the corresponding inductor period ends, due to the voltage stored in the capacitor. For example, as shown in FIG. 26, when the discharging portion 2612 ends, the voltage level of the switching output voltage at the third output portion begins to decrease (e.g., curve 2624 drops). As another example, as shown in FIG. 26, when the charging portion 2608c ends, the voltage level of the switching output voltage at the first output portion begins to decrease (e.g., curve 2620 drops). As shown in FIG. 26, electrically coupling the inductor to the first output portion for each inductor period can reduce the voltage ripple at the first output.

[0222] FIG. 27 shows a flowchart of an exemplary method 2700 for operating a single inductor multiple output converter in accordance with at least one aspect described in the present disclosure. The method 2700 may include one or more blocks 2702, 2704, 2706, 2708, or 2710. Although shown as separate blocks, the operations associated with one or more of the blocks of the method 2700 may, depending on the particular implementation, be further divided into additional blocks, combined into fewer blocks, or removed.

[0223] In block 2702, the method may include controlling (e.g., switching) a switch. In some aspects of the present disclosure, the switch may supply a switched output voltage in response to an input current supplied to an inductor.

[0224] In block 2704, the method may include controlling the switched output voltage. In some aspects of the present disclosure, the method may include controlling the switch to control the switched output voltage.

[0225] In block 2706, the method may include applying the switched output voltage to a converter output. In some aspects of the present disclosure, the method may include applying the switched output voltage to a single converter output during a charging or discharging portion of an inductor cycle.

[0226] In block 2708, the method may include applying the switched output voltage to a first converter output. In some aspects of the present disclosure, the method may include applying the switched output voltage to the first converter output during a first time portion of a first duty cycle. In these and other aspects of the present disclosure, the first time portion of the first duty cycle may correspond to a charging portion of an inductor cycle.

[0227] In block 2710, the method may include applying the switched output voltage to another converter output. In some aspects of the present disclosure, the method may include applying the switched output voltage to a converter output other than the first converter output. In these and other aspects of the present disclosure, the method may include applying the switched output voltage to a converter output other than the first converter output during a second time portion of the first duty cycle. In these and other aspects of the present disclosure, the second time portion of the first duty cycle may correspond to a discharging portion of an inductor cycle.

[0228] Modifications, additions, or omissions may be made to method 2700 without departing from the scope of the present disclosure. For example, the operations of method 2700 may be performed in a different order. Additionally, or alternatively, two or more operations may be executed simultaneously. Further, the operations and actions described are provided as an example by way of illustration, and some of the operations and actions may be optional, may be combined into fewer operations and actions, or may be extended to additional operations and actions without departing from the essence of the described embodiments.

[0229] FIG. 28 shows a graphical representation 2800 of a simulation including a timing diagram of switches in a SIMO converter, including the electrical coupling of an inductor to two electrical devices during separate inductor cycles, according to at least one embodiment described in the present disclosure.

[0230] In FIG. 28, waveforms 2606a - e represent the current in the inductor during the inductor cycle, as described above in relation to FIG. 26. Further, in FIG. 28, curves 2620, 2622, 2624, 2626, and 2628 show how the switching output voltage at each converter output of the SIMO converter changes by charging or discharging the inductor during the inductor cycle, as described above in relation to FIG. 26.

[0231] Curves 2801, 2803, 2805, 2807, 2809, 2811, and 2813 show the timing diagrams of the voltage (e.g., gate voltage) at one or more gates of the switches in the SIMO converter. Curve 2801 corresponds to the gate voltage at the gate of the high - side portion of the switch of the SIMO converter. In some embodiments of the present disclosure, the high - side portion of the switch of the SIMO converter may correspond to the switch that controls the charging of the inductor. Curve 2803 corresponds to the gate voltage at the gate of the low - side portion of the switch in the SIMO converter. In some embodiments of the present disclosure, the low - side portion of the switching of the SIMO converter may correspond to the switch that controls the discharging of the inductor.

[0232] Curves 2805, 2807, 2809, 2811, and 2813 correspond to the gate voltage at the gate of the switch with respect to the converter output of the SIMO converter.

[0233] As shown in FIG. 28, when the gate voltage of the high-side portion (e.g., curve 2801) is high, the charging portions 2608a to 2608e appear. Further, when the gate voltage of the high-side portion (e.g., curve 2801) is low, the charging portions 2608a to 2608e do not appear. Further, as shown in FIG. 28, when the gate voltage at the gate of the low-side portion (e.g., curve 2803) is high, one of the discharging portions 2610, 2612, 2614, 2616, and 2618 appears. When the gate voltage of the low-side portion (e.g., 2803) is low, the discharging portions 2610, 2612, 2614, 2616, and 2618 do not appear.

[0234] As shown in FIG. 28, when the gate voltage at the gate of the switch in the converter output of the SIMO converter is high, the voltage level of the switching output voltage at the corresponding converter output increases. For example, when curve 2805 is high, curve 2620 increases. As another example, when curve 2807 is high, curve 2622 increases. As yet another example, when curve 2809 is high, curve 2624 increases. As another example, when curve 2811 is high, curve 2626 increases. As another example, when curve 2813 is high, curve 2628 increases.

[0235] As shown in FIG. 28, when the gate voltage at the gate of the switch for the converter output section of the SIMO converter is low, the voltage level of the switching output voltage at the corresponding converter output section decreases or becomes substantially zero volts. For example, when curve 2805 is low, curve 2620 decreases. As another example, when curve 2807 is low, curve 2622 decreases. As yet another example, when curve 2809 is low, curve 2624 decreases. As another example, when curve 2811 is low, curve 2626 decreases. As another example, when curve 2813 is low, curve 2628 decreases.

[0236] As shown in FIG. 28, each charging portion of the inductor period can occur when curves 2801 and 2805 are high and curve 2803 is low. Each discharging portion of the inductor period can occur when curves 2801 and 2805 are low and curve 2803 is high. Further, each discharging portion of the inductor period appears when one or more of curves 2807, 2809, 2811, and 2813 are high (for example, when the corresponding gate voltage at the gate of the switch for the converter output section of the SIMO converter is high).

[0237] The separated inductor periods 2606a to e can reduce the ripple at the first converter output section (for example, curve 2620) by supplying the switching output voltage at the first converter output section for each of the separated inductor periods 2606a to e. The voltage ripple of the switching output voltage at the first converter output section (also referred to as the ripple value in this specification) (for example, the difference between the high point and the low point of curve 2620) can be lower than the ripple of the switching output voltage at the second converter output section, the third converter output section, the fourth converter output section, the fifth converter output section, or any combination thereof (for example, the difference between the high point and the low point of curve 2622, 2624, 2626, 2628, or any combination thereof).

[0238] FIG. 29 shows a block diagram of an exemplary system 2900 that includes a SIMO converter 104, in accordance with at least one aspect described in the present disclosure. The system 2900 may include a SIMO converter 104, one or more ripple sensors (also referred to as ripple detectors) 2915a - e, a switch controller 2917, and a level shifter 2919.

[0239] The system 2900 may include one or more LDOs (not shown). In some aspects of the present disclosure, the LDO may correspond to the LDO 106 described elsewhere in the present disclosure.

[0240] In FIG. 29, for the sake of brevity of illustration and discussion, only one switch controller 2917 is shown and discussed. In some aspects of the present disclosure, the system 2900 may include multiple switch controllers 2917. In other aspects of the present disclosure, the system 2900 may include only one ripple detector 2915 electrically coupled to one or more converter output portions of the SIMO converter 104.

[0241] The SIMO converter 104 may correspond to the SIMO converter 104 described elsewhere in the present disclosure. The SIMO converter 104 may include multiple output portions to supply the switching output voltage 108 at different values at the converter output.

[0242] The ripple detectors 2915a - e may detect the ripple of the switching output voltage at the corresponding converter output. The ripple detectors 2915a - e may determine the ripple value of the ripple of the switching output voltage at the corresponding converter output. For example, the ripple detector 2915a may determine the ripple value of the ripple of the switching output voltage 108a at the first converter output. The ripple detectors 2915a - e may generate a ripple voltage 2817 based on the corresponding ripple value of the ripple of the switching output voltage. For example, the ripple detector 2915a may generate a ripple voltage based on the ripple value of the ripple of the switching output voltage 108a at the first converter output.

[0243] The switch controller 2917 may be configured to control the switches within the SIMO converter 104. The switch controller 2917 may control the switches within the SIMO converter 104 to selectively apply the switching output voltage 108 to the converter output section.

[0244] The switch controller 2917 may generate one or more switch voltages 2911 based on the ripple voltage 2817 and the clock voltage 2103. In some aspects of the present disclosure, when the ripple voltage 2817 is logic high and the clock voltage 2103 is received, the switch controller 2917 may generate the switch voltage 2911 such that the high-side portion of the SIMO converter 104 turns off and the low-side portion and the corresponding output switch within the SIMO converter 104 turn on.

[0245] The level shifter 2919 may receive the switch voltage 2911. The level shifter 2919 may shift one or more voltage levels of the switch voltage 2911 to levels sufficient to transition the corresponding switches within the SIMO converter 104 between an open position and a closed position. The level shifter 2919 may generate a gate voltage based on the switch voltage 2911. In some aspects of the present disclosure, the level shifter 2919 may delay the gate voltage 2913 based on the corresponding stage of the SIMO converter 104 that is to receive the gate voltage 2913.

[0246] A system including a master controller and / or a switch controller may operate such that the voltage ripple of one or more switching output voltages of an output of a SIMO converter is controlled. In some aspects of the present disclosure, the master controller and / or the switch controller may control the duty cycle of one or more switches in the SIMO converter, such that the switch is in the closed position more frequently than other switches in the SIMO converter. The voltage ripple may be controlled based on the voltage ripple requirements of an electrical device electrically coupled to the corresponding output of the SIMO converter.

[0247] In some aspects of the present disclosure, the master controller may be electrically coupled to a switching output voltage (e.g., one or more outputs of a SIMO converter). In these and other aspects of the present disclosure, the master controller may determine the voltage level of the switching output voltage at each output of the SIMO converter. Further, the master controller may supply a signal to the switch controller such that the duty cycle of the switch is controlled to reduce or regulate the voltage ripple of the switching output voltage at one or more outputs of the SIMO converter.

[0248] In some aspects of the present disclosure, the master controller may not be electrically coupled to the switching output voltage. In these and other aspects of the present disclosure, the master controller may be programmed to supply a signal to the switch controller such that the duty cycle of the switches in the SIMO is controlled to automatically reduce or control the voltage ripple of the switching output voltage at one or more outputs of the SIMO.

[0249] The switch controller may be configured to control the switches in the SIMO converter to control the switching output voltage. For example, the switch controller may control the duty cycle of the switches in the SIMO converter. In some aspects of the present disclosure, the switch controller may control the switches in the SIMO converter such that the switching output voltage can be applied to the first converter output of the SIMO converter during the first time portion of the duty cycle (e.g., the inductor period). In these and other aspects of the present disclosure, the first time portion of the duty cycle may correspond to the charging portion of the inductor period. Further, the switch controller may control the switches in the SIMO converter such that the inductor in the SIMO converter is charged during the first time portion of the duty cycle. For example, the switch controller may control the switches in the SIMO converter such that the inductor is charged (e.g., energized) and the switching output voltage is applied to the first converter output of the SIMO converter between the first time portion of the first duty cycle and the first time portion of the second duty cycle. In some aspects of the present disclosure, the second duty cycle may occur immediately following the first duty cycle.

[0250] In some aspects of the present disclosure, the switch controller may control the switches in the SIMO converter to apply the switching output voltage to the second converter output of the SIMO converter during the second time portion of the duty cycle. In other aspects of the present disclosure, the second time portion may correspond to the discharge portion of the inductor cycle. In some aspects of the present disclosure, the switch controller may control the switches in the SIMO converter to apply the switching output voltage to the converter output of the SIMO converter other than the first converter output during the second time portion. For example, when the switching output voltage is applied to the first converter output during the first time portion of the duty cycle, the switch controller may control the switches in the SIMO converter to apply the switching output voltage to the second converter output, the third converter output, or the fourth converter output of the SIMO during the second time portion of the duty cycle. As another example, when the SIMO converter applies the switching output voltage to the first converter output during the first time portion of the duty cycle, the switch controller may control the switches in the SIMO converter to apply the switching output voltage to the second converter output during the second time portion of the second duty cycle and to apply the switching output voltage to the third converter output during the second time portion of the third duty cycle.

[0251] In some aspects of the present disclosure, the ripple of the switching output voltage may be automatically controlled. For automatic control, a ripple detector may detect the ripple of the switching output voltage at the converter output. The ripple detector may determine the ripple value of the ripple of the switching output voltage at the converter output. Further, the ripple detector may generate a ripple voltage based on the ripple value.

[0252] The switch controller may receive a ripple voltage. The switch controller may generate a switch voltage based on the ripple voltage. The switch controller may control a switch in the SIMO converter based on the voltage level of the switch voltage. The switch voltage may be adjusted such that the energization phase of the inductor period corresponding to reducing the ripple of the switching output voltage is also adjusted. The level shifter may receive the switch voltage. Further, the level shifter may shift one or more voltage levels of the switch voltage to a level sufficient to transition the corresponding switch in the SIMO converter between an open position and a closed position.

[0253] The switch controller automatically controlling the ripple of the switching output voltage may enable the ripple to be dynamically regulated. Further, the switch controller automatically controlling the ripple of the switching output voltage may keep the ripple of the switching output voltage within bounds by adjusting the energization phase of the corresponding inductor period.

[0254] In another aspect of the present disclosure, the switch controller may monitor the ripple of the switching output voltage. The switch controller may reserve one or more time slots corresponding to the energization phase for a converter output with a higher priority. The switch controller reserving the time slots may reduce the ripple of the switching output voltage at the corresponding converter output.

[0255] The sequence and mode selector may select the operating mode of the SIMO converter 104. The sequence and mode selector may select the operating mode so as to prioritize various factors of the SIMO converter 104 or the switching output voltage. For example, the sequence and mode selector may select the operating mode so as to prioritize the efficiency of the SIMO converter 104, the transient response of the switching output voltage, or the ripple of the switching output voltage. The sequence and mode selector may prioritize the transient response of the switching output voltage so as to improve the transient response of the switching output voltage. Further, the sequence and mode selector may prioritize the ripple of the switching output voltage so as to reduce the ripple of the switching output voltage.

[0256] Power management can include a wide variety of aspects that may depend, for example, on the nature of the device to be powered or its various components. One or more of these power management aspects may be more important than others, depending on the implementation. For example, in a small portable device (e.g., a battery-powered device with a small battery), efficiency may be important, while in a device with a large battery or a reliable power source, ripple reduction may be more important than efficiency. The SIMO buck-boost converter can use various operating modes, and one operating mode prioritizes one or more power management factors (e.g., battery management, efficiency, ripple reduction, transient response, etc.). The sequence and mode selector may select the operating mode of the SIMO converter so as to prioritize various factors of the SIMO converter or to supply the switching output voltage to the converter output within the voltage domain or within the operating parameters of the associated electronic device.

[0257] FIG. 30 shows a block diagram of an exemplary system 3000 that includes a SIMO converter 104, in accordance with at least one aspect described in the present disclosure. System 3000 may also include a switch controller 3002, a sequence and mode selector 3004, a current sensor 3008, and a power management (PM) circuit 3006. In FIG. 30, for the sake of brevity of illustration and discussion, only one switch controller 3002 is shown and discussed. In some aspects of the present disclosure, system 3000 may include only one switch controller 3002 as shown in FIG. 30. In other aspects of the present disclosure, system 3000 may include two or more switch controllers 3002.

[0258] In some aspects of the present disclosure, the SIMO converter 104 may correspond to the SIMO converter 104 described elsewhere in the present disclosure. In some aspects of the present disclosure, the SIMO converter 104 may include multiple output sections to supply switching output voltages 108a - n at different values at two or more converter output sections. In some aspects of the present disclosure, system 3000 may include one or more LDOs (not shown). In some aspects of the present disclosure, the LDO may correspond to the LDO 106 described elsewhere in the present disclosure.

[0259] In some aspects of the present disclosure, the current sensor 3008 may be electrically coupled between the first terminal of the inductor 202 and the sequence and mode selector 3004. In these and other aspects of the present disclosure, the sequence and mode selector 3004 may be electrically coupled to the PM circuit 3006 and / or the switch controller 3002. Further, in some aspects of the present disclosure, the sequence and mode selector 3004 may be communicatively coupled to the PM circuit 3006 and / or the switch controller 3002. Further, in some aspects of the present disclosure, the switch controller 3002 may be electrically coupled to one or more of the switches 204a-n, 206, 208, 210 within the SIMO converter 104. In FIG. 30, the switch controller 3002 is shown as being coupled to a dashed rectangle, rather than to each of the switches 204a-n, 206, 208, 210, for the sake of brevity of illustration.

[0260] In some aspects of the present disclosure, the PM circuit 3006 may generate a target request. In these and other aspects of the present disclosure, the target request may include a power / current split command, an efficiency requirement command, and / or a ripple requirement command. Further, in some aspects of the present disclosure, the target request may indicate whether the efficiency of the SIMO converter or the ripple or transient response of the switching output voltage at a particular converter output is to be prioritized. In some aspects of the present disclosure, the PM circuit 3006 may supply the target request to the sequence and mode selector 3004.

[0261] The sequence and mode selector 3004 may receive a target request from the PM circuit. In some aspects of the present disclosure, the sequence and mode selector 3004 may select an operating mode of the SIMO converter 104 for one or more converter output sections based on the target request. In these and other aspects of the present disclosure, the sequence and mode selector 3004 may select an operating mode of the SIMO converter 104 for one or all of the converter output sections. For example, the sequence and mode selector 3004 may select an operating mode of the SIMO converter 104 for all of the converter output sections to prioritize the transient response of the switching output voltage. As another example, the sequence and mode selector 3004 may select an operating mode of the SIMO converter 104 for the first converter output section to prioritize the ripple of the switching output voltage, and may also select an operating mode of the SIMO converter 104 for the second converter output section to prioritize the efficiency of the SIMO converter 104.

[0262] In some aspects of the present disclosure, the sequence and mode selector 3004 may instruct the switch controller 3002 to control the switches 204a~n, 206, 208, and 210 according to the selected operating mode. In these and other aspects of the present disclosure, the switch controller 3002 may control the switches 204a~n, 206, 208, and 210 according to the selected operating mode. In these and other aspects of the present disclosure, the switch controller 3002 may control the duty cycles of the switches 204a~n, 206, 208, and 210 to control the switching output voltage at the corresponding converter output section (e.g., the corresponding rail). In some aspects of the present disclosure, the switch controller 3002 may control the switches 204a~n, 206, 208, and 210 to operate the SIMO converter 104 according to the selected operating mode.

[0263] In some aspects of the present disclosure, the current sensor 3008 may detect the current in the inductor 202. In these and other aspects of the present disclosure, the current sensor 3008 may detect the current in the inductor 202 during an energizing phase, a de-energizing phase, or a discharge period. In these and other aspects of the present disclosure, the sequence and mode selector 3004 may determine the current value of the current in the inductor 202 based on the detected current. In some aspects of the present disclosure, the current sensor 3008 may determine the current value of the current in the inductor 202 based on the detected current. Further, in some aspects of the present disclosure, the sequence and mode selector 3004 may select the operating mode of the SIMO converter 104 based on the current value of the current in the inductor (e.g., the inductor current) and / or a target request.

[0264] FIG. 31 shows a block diagram of another exemplary system 3100 that includes a SIMO converter 104 in accordance with at least one aspect described in the present disclosure. In some aspects of the present disclosure, the system 3100 may also include a switch controller 3002, a sequence and mode selector 3004, a current sensor 3008, and a PM circuit 3006. Further, the system 3100 may include a ripple detector 3110.

[0265] In FIG. 31, for the sake of brevity of illustration and discussion, only one switch controller 3002 and one ripple detector 3110 are shown and discussed. In some aspects of the present disclosure, the system 3100 may include only one switch controller 3002 and one ripple detector 3110 as shown in FIG. 31. In other aspects of the present disclosure, the system 3100 may include one or more switch controllers 3002 or one or more ripple detectors 3110.

[0266] In some aspects of the present disclosure, system 3100 may operate similarly to system 3000 described in connection with FIG. 30, except that it includes a ripple detector 3110. In some aspects of the present disclosure, ripple detector 3110 may be electrically coupled to different converter output portions of SIMO converter 104.

[0267] In some aspects of the present disclosure, ripple detector 3110 may detect ripple of the switching output voltage at one or more of the converter output portions. In these and other aspects of the present disclosure, sequence and mode selector 3004 may determine a ripple value of the ripple of the switching output voltage at the converter output portion based on the detected voltage ripple. In some aspects of the present disclosure, ripple detector 3110 may determine a ripple value of the ripple of the switching output voltage based on the detected voltage ripple. Further, in some aspects of the present disclosure, sequence and mode selector 3004 may select an operating mode of SIMO converter 104 based on a target request, a current value of a current in an inductor (e.g., inductor current), and / or a ripple value of the ripple of the switching output voltage.

[0268] FIG. 32 shows a flowchart of an exemplary method 3200 for operating a SIMO converter for sequence and mode selection in accordance with at least one aspect described in the present disclosure. Method 3200 may include one or more blocks 3202 to 3222. Although shown as separate blocks, operations associated with one or more of the blocks of method 3200 may be divided into further blocks, combined into fewer blocks, or omitted, depending on a particular implementation.

[0269] Method 3200 may include, at block 3202, detecting an input from the PM circuit. In some aspects of the present disclosure, sequence and mode selector 3004 may detect an input from PM circuit 3006. In some aspects of the present disclosure, the input may include a target request. In some aspects of the present disclosure, block 3204 may follow block 3202.

[0270] Method 3200 may include, at block 3204, determining whether the mode in the input is set to efficiency. In some aspects of the present disclosure, sequence and mode selector 3004 may determine whether the mode in the input is set to efficiency. In some aspects of the present disclosure, the target request may indicate that efficiency of the SIMO converter should be prioritized at the corresponding converter output. For example, an electronic device electrically coupled to the corresponding converter output may include a specific efficiency setting for proper operation. If the mode in the input is set to efficiency, block 3204 may be followed by block 3206. If the mode in the input is not set to efficiency, block 3204 may be followed by block 3208.

[0271] The method 3200 may include initiating discontinuous conduction mode (DCM) at block 3206. In some aspects of the disclosure, the sequence and mode selector 3004 may instruct the switch controller to control the switches 204a-n, 206, 208, and / or 210 in the SIMO converter 104 according to DCM operation. In some aspects of the disclosure, the DCM operation of the SIMO converter for one or more converter outputs may include charging an inductor with a separate inductor cycle and discharging the inductor with a corresponding converter output, as described elsewhere in this disclosure.

[0272] Method 3200 may include, at block 3208, determining whether the mode in the input is set to ripple. In some aspects of the present disclosure, sequence and mode selector 3004 may determine whether the mode in the input is set to ripple. In some aspects of the present disclosure, a target request may indicate that management of the ripple of the switching output voltage at a corresponding converter output (e.g., a corresponding SIMO converter rail) should be prioritized. If the mode in the input is set to ripple, block 3212 may follow block 3208. If the mode in the input is not set to ripple, block 3214 may follow block 3208.

[0273] Method 3200 may include, at block 3210, detecting the ripple of the switching output voltage. In some aspects of the present disclosure, ripple detector 3110 may detect the ripple of the switching output voltage. In some aspects of the present disclosure, the ripple of the switching output voltage may be detected at a corresponding converter output.

[0274] Method 3200 may include, at block 3212, determining whether the ripple is below a threshold. In some aspects of the present disclosure, sequence and mode selector 3004 may determine whether the ripple is below a threshold. In some aspects of the present disclosure, the threshold of the ripple of the switching output voltage may include ~5 to 10 mV, ~5 to 15 mV, ~5 to 20 mV, or ~5 to 25 mV, depending on the voltage domain and its noise requirements. In these and other aspects of the present disclosure, method 3200 may include setting the threshold of the ripple of the switching output voltage to a predefined value. In other aspects of the present disclosure, method 3200 may include setting the threshold of the ripple of the switching output voltage statically or dynamically. If the ripple of the switching output voltage is below the threshold, block 3206 may follow block 3212. If the ripple of the switching output voltage is equal to or above the threshold, block 3218 may follow block 3212.

[0275] Method 3200 may include, at block 3214, determining whether the mode within the input is set to transient response. In some aspects of the present disclosure, sequence and mode selector 3004 may determine whether the mode within the input is set to transient response. In some aspects of the present disclosure, a target request may indicate that management of the transient response of the switching output voltage at a corresponding converter output (e.g., a corresponding SIMO converter rail) should be prioritized. If the mode within the input is set to transient response, block 3206 may follow block 3214. If the mode within the input is not set to transient response, block 3202 may follow block 3214.

[0276] Method 3200 may include, at block 3216, detecting current or voltage at the rail. In some aspects of the present disclosure, sequence and mode selector 3004 and / or current sensor 3008 may detect current or voltage at the inductor. In some aspects of the present disclosure, the current or voltage may be detected at one or more converter outputs.

[0277] Method 3200 may include, at block 3218, determining whether the power at the rail is below a threshold. In some aspects of the present disclosure, sequence and mode selector 3004 may determine whether the power at the rail is below a threshold. In some aspects of the present disclosure, the power at the rail may be determined as the product of the detected current and voltage at the rail. In these and other aspects of the present disclosure, the power level may be <10% of ICC MAX assuming the rail current is supplied in DCM. The power level may be understood as a percentage of the maximum current supported by the rail. Alternatively, the power level may be described as a percentage of the inductor current rating.

[0278] In these and other aspects of the present disclosure, method 3200 may include setting a threshold of power on the rail to a predefined value. In other aspects of the present disclosure, method 3200 may include setting the threshold of power on the rail dynamically or statically. If the power on the rail falls below the threshold, block 3220 may follow block 3218. If the power on the rail is equal to or above the threshold, block 3222 may follow block 3218.

[0279] Method 3200 may include, at block 3220, starting a hybrid continuous conduction mode (CCM). In some aspects of the present disclosure, sequence and mode selector 3004 may instruct the switch controller to control switches 204a - n, 206, 208, and / or 210 in SIMO converter 104 according to the hybrid CCM operation. In some aspects of the present disclosure, the hybrid CCM operation of the SIMO converter may include charging the inductor using both discrete inductor periods and continuous inductor periods and discharging the inductor by a corresponding converter output, as described elsewhere in the present disclosure.

[0280] Method 3200 may include, at block 3222, starting a CCM operation. In some aspects of the present disclosure, sequence and mode selector 3004 may instruct the switch controller to control switches 204a - n, 206, 208, and / or 210 in SIMO converter 104 according to the CCM operation. In some aspects of the present disclosure, the CCM operation of the SIMO converter may include charging the inductor using continuous inductor periods and discharging the inductor by a corresponding converter output, as described elsewhere in the present disclosure.

[0281] In some aspects of the present disclosure, method 3200 may be executed while maintaining the current operating mode of the SIMO converter for the corresponding converter output. For example, method 3200 may be executed when the SIMO converter for the corresponding converter output is already operating in DCM, hybrid CCM, or CCM. In these and other aspects of the present disclosure, method 3200, block 3206, block 3220, or block 3222 may include maintaining the current operating mode of the corresponding converter output when the SIMO converter is already operating according to the current operating mode for one or more converter outputs.

[0282] Changes, additions, or omissions may be made to method 3200 without departing from the scope of the present disclosure. For example, the operations of method 3200 may be performed in a different order. Additionally, or alternatively, two or more operations may be performed simultaneously. Further, the operations and actions described are provided as examples only, and some of the operations and actions may be optional, combined into fewer operations and actions, or extended to additional operations and actions without departing from the essence of the described aspects.

[0283] FIG. 33 shows graphical representations 3312 and 3318 of simulations in which a SIMO converter operates in hybrid CCM or hybrid DCM and CCM during an inductor period, according to at least one aspect described in the present disclosure. In FIG. 33, graphical representation 3312 may represent a simulation in which the SIMO converter operates in hybrid CCM for a plurality of converter outputs of the SIMO converter. Further, graphical representation 3318 may represent a simulation in which the SIMO converter operates in hybrid DCM and CCM for a plurality of converter outputs of the SIMO converter.

[0284] Regarding graph representation 3312, waveforms 3314a, b and 3316a, b represent the current in the inductor during the inductor period. Waveforms 3314a, b and 3316a, b show how the current in the inductor changes over time during the inductor period. As shown in FIG. 33, waveforms 3316a, b show the inductor period during which the inductor is electrically coupled during the inductor period corresponding to one electrical device (e.g., device 1). Further, as shown in FIG. 33, waveforms 3314a, b show the inductor period during which the inductor is electrically coupled during the inductor period corresponding to a plurality of electrical devices (e.g., device 2, device 3, and device 4). In some aspects of the present disclosure, the SIMO converter may operate in hybrid CCM with respect to the converter output when the power at one or more rails (e.g., the converter output) is below a threshold, as described above in connection with FIG. 32.

[0285] Regarding graph representation 3318, waveforms 3320a - c show the current in the inductor during the inductor period according to CCM and DCM. Waveforms 3320a - c show how the current in the inductor changes over time during the inductor period. As shown in FIG. 33, waveforms 3320a, c show the inductor period during which the inductor is charged according to CCM and discharged by the corresponding converter output. Further, as shown in FIG. 33, waveform 3320b includes periods 3322a, b representing the inductor period during which the inductor is charged according to DCM and discharged by the corresponding converter output.

[0286] In some aspects of the present disclosure, a SIMO converter can transition between CCM and DCM for a corresponding converter output based on a transition request. In these and other aspects of the present disclosure, a SIMO converter can transition between hybrid CCM, DCM, and between hybrid DCM and CCM for a corresponding converter output. For example, a SIMO converter can charge an inductor and discharge the inductor by a corresponding converter output as represented by graph representation 3312 during a period. As another example, a SIMO converter can charge an inductor and discharge the inductor by a corresponding converter output as represented by graph representation 3312 during a first period, and can also charge an inductor and discharge the inductor by a corresponding converter output as represented by graph representation 3318 during a second period.

[0287] FIG. 34 shows a graphical representation 3400 of a change in prioritization of different power rails within a SIMO converter in accordance with at least one aspect described in the present disclosure. In FIG. 34, over time, waveform 3424 shows the sequence of prioritization of the first rail (e.g., Rail1) of the SIMO converter, and waveform 3426 shows the sequence of prioritization of the second rail (e.g., Rail2) of the SIMO converter.

[0288] First, the sequence and mode selector 3004 may set the operating mode of the SIMO converter for both the first rail and the second rail to prioritize the efficiency of the SIMO converter (in FIG. 34, Rai1→efficiency and Rail2→efficiency are shown). After the first period, the sequence and mode selector 3004 may set the operating mode of the SIMO converter for the first rail to prioritize the transient response of the switching output voltage at the corresponding rail (in FIG. 34, Rail1→transient response is shown). After the second period, the sequence and mode selector 3004 may set the operating mode of the SIMO converter for the second rail to prioritize the management of the output ripple of the switching output voltage at the corresponding rail (in FIG. 34, Rail2→output ripple is shown). After the third period, the sequence and mode selector 3004 may set the operating mode of the SIMO converter for the first rail to prioritize the management of the output ripple of the switching output voltage at the corresponding rail (in FIG. 34, Rail1→output ripple is shown).

[0289] FIG. 35 illustratively shows a flowchart of a method 3500 for operating a SIMO converter in accordance with at least one aspect described in the present disclosure. The method 3500 may include supplying a switching output voltage to a converter output by a switch in response to an input voltage supplied to an inductor 3502, controlling the switch to control the switching output voltage 3504, controlling the switch to apply the switching output voltage to the converter output 3506, selecting an operating mode of the SIMO converter based on a received operation target request, and instructing a switch controller to control the switch in accordance with the selected operating mode 3508, and controlling the switch in accordance with the selected operating mode 3510.

[0290] In some aspects of the present disclosure, a SIMO converter for a converter output section may operate according to one or more operating modes. In these and other aspects of the present disclosure, the SIMO converter may prioritize various aspects of the operation of the SIMO converter according to a selected operating mode. In some aspects of the present disclosure, the SIMO converter may prioritize the efficiency of the SIMO converter or the ripple (e.g., output ripple) or transient response of the switching output voltage at the corresponding converter output section.

[0291] In some aspects of the present disclosure, the SIMO converter may include a PM circuit and an operating mode selector (also referred to herein as a sequence and mode selector). The PM circuit may be communicatively coupled to the operating mode selector. In these and other aspects of the present disclosure, the PM circuit may generate an operation target request (also referred to herein as a target request). Further, in some aspects of the present disclosure, the PM circuit may supply the operation target request to the operating mode selector.

[0292] In some aspects of the present disclosure, an operation target request may include a request to select an operation mode of a SIMO converter for one or more converter outputs that result in a ripple of the switching output voltage of less than 5 - 10 mV, less than 5 - 15 mV, less than 5 - 20 mV, or less than 5 - 25 mV. The voltage range depends at least on whether the domain is digital or analog. Depending on the workload, there may be various thresholds that are essentially dynamic. Further, in some aspects of the present disclosure, an operation target request may include a request to select an operation mode of a SIMO converter for one or more converter outputs that result in an energy efficiency of at least 80 - 90%. This may depend on multiple factors, but regardless of the threshold, the percentage may vary according to the workload and system needs determined by the power management unit. Further, in some aspects of the present disclosure, an operation target request may include a request to select an operation mode of a SIMO converter for one or more converter outputs that result in a power-to-current ratio corresponding to a range of 10 - 20% of the maximum current (below this range, DCM occurs, and above this range, CCM occurs). The percentage can be dynamically changed as needed to enforce the desired state (DCM or CCM). In some aspects of the present disclosure, an operation target request may include a request to select an operation mode of a SIMO converter for one or more converter outputs that result in a cross-regulation of the switching output voltage of less than 1% of the rail's Vccnom (nominal Vcc). Each rail generally has a DC tolerance range of ±1%, so the cross-regulation will be well below this. However, 1% of Vccnom is generally the upper threshold. The lower the voltage, the generally narrower the DC tolerance range.

[0293] In some aspects of the present disclosure, the operation mode selector may receive an operation target request. In these and other aspects of the present disclosure, the operation mode selector may select an operation mode of the SIMO converter for one or more converter outputs from a plurality of operation modes. In these and other aspects of the present disclosure, the operation mode selector may select an operation mode of the SIMO converter for the converter output based on the received operation target request.

[0294] In some aspects of the present disclosure, the operation mode may include CCM, DCM, or an operation mode that provides a different scheduling scheme. In some aspects of the present disclosure, the different scheduling scheme may include a scheduling scheme in the order of selecting the converter outputs. Further, in some aspects of the present disclosure, the operation mode may include hybrid CCM or hybrid CCM and DCM. For example, the operation mode of SIMO for one or more converter outputs may include CCM, and the operation mode of SIMO for one or more other converter outputs may include DCM. Further, in some aspects of the present disclosure, the operation mode may include an operation mode configured to minimize cross-regulation between different converter outputs.

[0295] In some aspects of the present disclosure, the SIMO converter may include a current sensor and / or a ripple detector. In these and other aspects of the present disclosure, the current sensor may detect the current in the inductor (e.g., detect the inductor current). Further, in some aspects of the present disclosure, the ripple detector may detect the ripple of the switching output voltage at one or more converter outputs.

[0296] In some aspects of the present disclosure, the operation mode selector may determine the current value of the current in the inductor. In these and other aspects of the present disclosure, the operation mode selector may determine the operation mode based on the operation target request, the current in the inductor, or the current value of the current in the inductor.

[0297] In some aspects of the present disclosure, the operation mode selector may determine the power-to-current ratio. In these and other aspects of the present disclosure, the operation mode selector may determine the power consumption of the inductor by determining the product of the current in the inductor and the switching output voltage (e.g., the power is equal to the current in the inductor multiplied by the switching output voltage). Further, in some aspects of the present disclosure, the operation mode selector may compare the power to the current in the inductor to determine a ratio.

[0298] In some aspects of the present disclosure, the operation selector may generate a command signal indicating the selected operation mode of the SIMO converter for the converter output. In these and other aspects of the present disclosure, the operation selector may supply the command signal to the switch controller.

[0299] In some aspects of the present disclosure, the switch controller may control the switches of the SIMO converter according to the selected operation mode. In these and other aspects of the present disclosure, the switch controller may control the duty cycle of the switches to control one or more operation modes of the SIMO converter. For example, the switch controller may control the switches to control the ripple of the switching output voltage at one or more converter outputs during one or more inductor periods. As another example, the switch controller may control the switches to operate the SIMO converter according to CCM for one or more converter outputs and according to DCM for one or more other converter outputs.

[0300] In some aspects of the present disclosure, the switch controller may control the switches to minimize the cross-regulation of the switching output voltages at two or more converter outputs. In these and other aspects of the present disclosure, the switch controller may control the switches to enable efficient operation of the SIMO converter for one or more converter outputs.

[0301] In some aspects of the present disclosure, an operation target request may include a plurality of digital signals supplied by a PM circuit using a plurality of rails. One or more of the digital signals may include a logic high (e.g., equal to 1), which may indicate that a particular prioritization should be selected by the operation mode selector.

[0302] A voltage converter system may include a SIMO converter 104 and a digital circuit. The digital circuit may determine timing parameters for the duty cycle of a switch in the SIMO converter 104. The digital circuit may determine the timing parameters such that each duty cycle includes an energizing phase and a de-energizing phase with respect to an inductor in the SIMO converter 104.

[0303] In accordance with an aspect of the present disclosure, a SIMO buck-boost converter may use a digital circuit to control its switches. The digital circuit may utilize any of a plurality of strategies (e.g., timing, feedback, etc.) to control the switches to maintain an output voltage within the voltage domain of an electronic device coupled to the converter output.

[0304] FIG. 36 shows a block diagram of an exemplary system 3600 that includes a SIMO converter 104 in accordance with at least one aspect described in the present disclosure. System 3600 may also include a digital circuit 3602. In FIG. 36, for simplicity of illustration and discussion, only one block representing the digital circuit is shown and discussed.

[0305] In some aspects of the present disclosure, the SIMO converter 104 may correspond to the SIMO converter 104 described elsewhere in the present disclosure. In some aspects of the present disclosure, the SIMO converter 104 may include multiple output portions to supply the switching output voltages 108a-n at different values at two or more converter output portions. In some aspects of the present disclosure, the system 3600 may include one or more LDOs (not shown). In some aspects of the present disclosure, the LDO may correspond to the LDO 106 described elsewhere in the present disclosure.

[0306] In some aspects of the present disclosure, the digital circuit 3602 may include one or more analog-to-digital converters (ADCs), digital processors, or any other suitable circuits. In these and other aspects of the present disclosure, the digital circuit 3602 may be electrically coupled to one or more converter output portions. The digital circuit 3602 may receive the switching output voltage via the converter output portion. For example, one or more ADCs within the digital circuit 3602 may receive the switching output voltage via the converter output portion.

[0307] In some aspects of the present disclosure, the digital circuit 3602 may convert the switching output voltage into one or more digital switching output voltage values. In these and other aspects of the present disclosure, the one or more digital switching output voltage values may be digital signals representing the switching output voltage.

[0308] In some aspects of the present disclosure, the digital circuit 3602 (e.g., digital processor) may receive the switching output via one or more converter output portions. Further, in some aspects of the present disclosure, the digital circuit 3602 may receive one or more reference voltages (in FIG. 36, represented as V ref1 , V ref2 , V ref3 , V ref4 ). In these and other aspects of the present disclosure, the digital circuit 3602 may receive a reference voltage (e.g., associated target output voltage) for each converter output portion of the SIMO converter 104.

[0309] In some aspects of the present disclosure, the digital circuit 3602 may determine one or more timing parameters for the SIMO converter 104. In these and other aspects of the present disclosure, the digital circuit 3602 may determine a timing parameter related to the duty cycle of the SIMO converter 104. In these and other aspects of the present disclosure, the digital circuit 3602 may determine a timing parameter for the SIMO converter 104 based on a switching output voltage or a reference voltage. For example, the digital circuit 3602 may determine a timing parameter for the SIMO converter 104 based on a difference between one or more of the switching output voltage and the reference voltage.

[0310] In some aspects of the present disclosure, the digital circuit 3602 may determine a timing parameter related to the energization phase of one or more inductor cycles of the SIMO converter 104. In these and other aspects of the present disclosure, the digital circuit 3602 may determine a timing parameter related to the de-energization phase of one or more inductor cycles of the SIMO converter 104.

[0311] In some aspects of the present disclosure, the digital circuit 3602 may select a computer program to implement one or more software algorithms. In these and other aspects of the present disclosure, the digital circuit 3602 may use a computer program implementing a software algorithm to determine a timing parameter. In these and other aspects of the present disclosure, the digital circuit 3602 may select a computer program from among a plurality of computer programs.

[0312] In some aspects of the present disclosure, the digital circuit 3602 may control switches 204a-n, 206, 208, 210 according to determined timing parameters. In these and other aspects of the present disclosure, the digital circuit 3602 may control the duty cycles of switches 204a-n, 206, 208, 210 according to determined timing parameters. In some aspects of the present disclosure, the digital circuit 3602 may generate one or more duty signals (represented as V TON , V TO1 , V TO2 , V TO3 , and V TO4 in FIG. 36). In some aspects of the present disclosure, the duty signal V TON may control the duty cycle of the switch for charging the inductor 202. In these and other aspects of the present disclosure, the duty signals V TO1 , V TO2 , V TO3 , and V TO4 may control the duty cycles of switches 204a-n, respectively.

[0313] FIG. 37 illustratively shows a flowchart of a method 3700 for operating a SIMO converter according to at least one aspect described in the present disclosure. The method 3700 includes supplying a switched output voltage to a converter output in a duty cycle in response to an input voltage supplied to an inductor by a switch 3702, converting an analog switched output voltage to a digital switched output voltage value by at least one analog-to-digital converter 3704, receiving at least one digital switched output voltage value 3706, receiving a related target output voltage value for each converter output of a plurality of converter outputs 3708, and determining timing parameters related to the duty cycle, related to an energizing phase in which the inductor is energized and related to a de-energizing phase in which the inductor is de-energized, for each duty cycle 3710.

[0314] 38 illustrates an example flowchart 3800 of a method for operating a SIMO converter in accordance with at least one aspect described herein. Method 3800 may include one or more blocks 3802 through 3814. Although shown in separate blocks, operations associated with one or more of the blocks of method 3800 may be divided into additional blocks, combined into fewer blocks, or eliminated, depending on the particular implementation.

[0315] The method 3800 may include, at block 3802, initiating operation of a clock. In some aspects of the disclosure, the clock may include a clock signal that operates a SIMO converter, a digital circuit, a switch controller, or some combination thereof. Block 3802 may be followed by block 3804.

[0316] The method 3800, at block 3804, IN , L, V On , I On , and f SW Using t ONn The meaning of these parameters will be explained below in relation to equation (1). In some aspects of the present disclosure, the digital circuit may calculate an initial value of V in , L, V On , I On , and f SW Using t ONn You can also calculate the initial value of t ONn The initial value of t may represent the amount of time that the corresponding output switch should be in the closed position during the corresponding inductor period (e.g., the amount of time that the discharge portion of the corresponding inductor period should occur). The digital circuit may calculate t for one or more output switches. ONn In some aspects of the present disclosure, the digital circuit may determine a value of t as defined in Equation (1) or Equation (2) below: ONn We can calculate the initial value of

[0317] In some aspects of the present disclosure, the digital circuitry includes a V IN , L, f SW , V On, or may include predefined values for some combination thereof. In these and other aspects of the present disclosure, the digital circuit uses a voltage sensor, a current sensor, or any other suitable technique to determine V IN , L, f SW , V On , or some combination thereof. Block 3806 may follow block 3804.

[0318] Method 3800 may include, at block 3806, operating the SIMO converter using the calculated initial value of t ONn . In some aspects of the present disclosure, the digital circuit may cause a switch controller to control the switches within the SIMO converter. The digital circuit may cause the switch controller to control the switches such that the discharge portion of the corresponding inductor period is based on the calculated initial value of t ONn . Block 3808 may follow block 3806.

[0319] Method 3800 may include, at block 3808, determining whether all values of V On are high. In some aspects of the present disclosure, the digital circuit may determine whether all values of V On (e.g., the value of the switching output voltage at the converter output) are high. The digital circuit may determine that the value of V On is high when the value of V On exceeds a threshold value. In some aspects of the present disclosure, the threshold value of the value of V On may include from 1.7 V to 7 V, for example, from 3 V to 5 V. If all values of V On are high, block 3810 may follow block 3808. If not all values of V On are high, block 3806 may follow block 3808. Blocks 3806 and 3808 may be repeated until all values of V On are high.

[0320] Method 3800 may include, at block 3810, V Onand I On is detected, and t ONn The value of may be updated. In some aspects of the present disclosure, the digital circuit is V at the corresponding converter output On and I On may be detected. In these and other aspects of the present disclosure, the digital circuit is V On By detecting a predefined value of, V On may be detected. The digital circuit may use the detected V On and I On to update the value of t ONn . In some aspects of the present disclosure, the digital circuit may update the value of t ONn as defined by equation (1) or equation (2).

Equation

Equation

[0321] In Equation (2), V On may represent the switching output voltage at the corresponding converter output, I On may represent the current at the corresponding converter output, I PK may represent the peak current at the corresponding converter output, f SW may represent the frequency rate for controlling the output switch, and VIN may represent the input voltage of the q, SIMO converter. Block 3812 may follow block 3810.

[0322] Method 3800 may include, at block 3812, operating a SIMO converter using an updated value of t ONn In some aspects of the present disclosure, the digital circuitry may cause a switch controller to control switches in the SIMO converter. The digital circuitry may cause the switch controller to control the switches such that the discharge portion of the corresponding inductor period is based on the updated value of t ONn Block 3814 may follow block 3812.

[0323] Method 3800 may include, at block 3814, determining whether all values of V On are within regulation. In some aspects of the present disclosure, the digital circuitry may determine whether all values of V On (e.g., values of the switching output voltage at the converter output) are within a predefined range as discussed elsewhere in the present disclosure. If all values of V On are within regulation, block 3812 may follow block 3814. Blocks 3812 and 3814 may repeat until all values of V On are within regulation or the operation of the SIMO converter ends. If not all values of V On are within regulation, block 3810 may follow block 3214. Blocks 3810, 3812, and 3814 may repeat until all values of V On are within regulation.

[0324] In some aspects of the present disclosure, blocks 3082, 3804, 3806, and 3808 may correspond to an initialization or startup period of the SIMO converter. In these and other aspects of the present disclosure, blocks 3810, 3812, and 3814 may correspond to a steady-state operation period of the SIMO converter.

[0325] In some SIMO converter control techniques, a controller implementing an analog control method for a SIMO converter may include a linear controller, a comparator, or other types of devices. However, these SIMO converter control techniques may be limited by the bandwidth of the analog components within the controller. Further, these SIMO converter control techniques may use a high-precision comparator to operate properly. Using a high-precision comparator may increase the cost or complexity of the circuitry associated with the controller.

[0326] In accordance with one or more aspects described in this disclosure, a digital circuit may control the operation of a SIMO converter. In these and other aspects of this disclosure, the digital circuit may determine how much power is drawn into the inductor of the SIMO converter. In these and other aspects of this disclosure, the digital circuit may determine how the power stored in the inductor should be distributed among different converter output portions. Further, in some aspects of this disclosure, the digital circuit may determine timing parameters for inductor control (e.g., timing parameters for the charging and discharging phases of the inductor period).

[0327] In some aspects of this disclosure, the digital circuit may include one or more ADCs and / or one or more digital processors. In these and other aspects of this disclosure, the ADC may convert a switching output voltage into one or more digital switching output voltage values. In some aspects of this disclosure, the digital switching output voltage values may represent the voltage levels of the switching output voltage.

[0328] In some aspects of this disclosure, the digital processor may receive the digital switching output voltage values. Further, the digital processor may receive, for each converter output portion of the SIMO converter, a corresponding target output voltage value (e.g., a reference voltage). In these and other aspects of this disclosure, the digital processor may compare the digital switching output voltage values with one or more corresponding associated target output voltage values.

[0329] In some aspects of the present disclosure, a digital processor may determine the timing parameters of a SIMO converter. In these and other aspects of the present disclosure, the digital processor may determine the timing parameters (e.g., inductor period) of the SIMO converter that are related to one or more duty cycles of the SIMO converter. Further, in some aspects of the present disclosure, the digital processor may determine the timing parameters using at least one digital switching output voltage value within the duty cycle of the SIMO converter. In other aspects of the present disclosure, the digital processor may determine the timing parameters using the digital switching output voltage value or the target output voltage value (e.g., the associated reference voltage) associated with each within the duty cycle of the SIMO converter.

[0330] In some aspects of the present disclosure, the digital processor may compare the digital switching output voltage value with the corresponding target output voltage value (e.g., the corresponding reference voltage). In these and other aspects of the present disclosure, the digital processor may determine whether the switching output voltage value is equal to the target output voltage value. In these and other aspects of the present disclosure, the timing parameters of the SIMO converter may be determined based on the difference between the digital switching output voltage value and the corresponding target output voltage value.

[0331] In some aspects of the present disclosure, the timing parameters may include the duration of the energization phase of the inductor period. In these and other aspects of the present disclosure, the digital processor may determine at least one energization time. Further, in some aspects of the present disclosure, the energization time may represent the duration for which the inductor is energized. In these and other aspects of the present disclosure, the digital processor may determine the energization time using at least one digital switching output voltage value within the duty cycle of the SIMO converter. In some aspects of the present disclosure, the digital processor may determine the energization time for each successive duty cycle of the SIMO converter.

[0332] In some aspects of the present disclosure, the timing parameter may include the duration of the decay phase of the inductor period. In these and other aspects of the present disclosure, the digital processor may determine at least one decay time. Further, in some aspects of the present disclosure, the decay time may represent the duration during which the inductor is decayed using at least one converter output of the SIMO converter. In these and other aspects of the present disclosure, the digital processor may determine the decay time using at least one digital switching output voltage value or the target output voltage value associated therewith within the duty cycle of the SIMO converter. In some aspects of the present disclosure, the digital processor may determine the decay time for each successive duty cycle of the SIMO converter.

[0333] In some aspects of the present disclosure, the timing parameter (e.g., the energization time or the decay time) may be determined to determine an amount for adjusting the duty cycle of the switch within the SIMO converter. In these and other aspects of the present disclosure, the duty cycle of the switch within the SIMO converter may be adjusted to increase or decrease the voltage level of the switching output voltage. In these and other aspects of the present disclosure, the duty cycle of the switch within the SIMO converter may be adjusted to increase or decrease the amount of energy stored in the inductor within the SIMO converter.

[0334] In some aspects of the present disclosure, the digital processor may determine the timing parameter using one or more software algorithms. In these and other aspects of the present disclosure, the digital processor may implement a software algorithm. In these and other aspects of the present disclosure, the digital processor may determine the energization time or the decay time using a software algorithm.

[0335] In some aspects of the present disclosure, a digital processor may select a computer program that implements a software algorithm. In these and other aspects of the present disclosure, the digital processor may select a computer program from among a plurality of computer programs. Further, in some aspects of the present disclosure, each of the computer programs may implement one or more software algorithms configured to determine timing parameters. In these and other aspects of the present disclosure, the digital processor may use the computer program to determine timing parameters with respect to various optimization criteria of the SIMO converter. In these and other aspects of the present disclosure, the digital processor may use the computer program to determine an energization time or a de-energization time with respect to various optimization criteria of the SIMO converter.

[0336] In some aspects of the present disclosure, the digital processor may be electrically coupled to a switch within the SIMO converter. In these and other aspects of the present disclosure, the digital processor may control the switch within the SIMO converter according to the determined timing parameter (e.g., energization time or de-energization time).

[0337] In other aspects of the present disclosure, the digital processor may be communicatively coupled to a switch controller that is electrically coupled to a switch within the SIMO converter. In these and other aspects of the present disclosure, the digital processor may instruct the switch controller to control the switch within the SIMO converter according to the determined timing parameter (e.g., energization time or de-energization time).

[0338] In some aspects of the present disclosure, one or more of the ADCs within the digital circuit may include an ADC based on a voltage controlled oscillator.

[0339] At least one aspect of the present disclosure may provide a controller for a SIMO converter that implements a computational method for determining timing parameters using a digital circuit. In these and other aspects of the present disclosure, the digital circuit may determine timing parameters over one or more clock cycles. Further, in some aspects of the present disclosure, the digital circuit may provide faster settling times, simpler circuit configurations, or greater process portability for SIMO converter control techniques that include analog circuits. Further, in some aspects of the present disclosure, the digital circuit may not include an analog regulator (e.g., it may not be necessary).

[0340] In some aspects of the present disclosure, the digital processor may determine the value of t for the output switch associated with each converter output. ONn The digital processor may determine the value of t by digital calculation in one clock cycle. ONn The value of can be determined.

[0341] In some aspects of the present disclosure, when the value of I PK is already known (e.g., available from a delay line), Equation (2) may reduce the computational cost of the digital processor compared to Equation (1).

[0342] The converter provides control of different switching output voltages according to the requirements associated with different electronic devices electrically coupled to the converter output. In some aspects of the present disclosure, each switching output voltage is associated with a peak current reference. The switch controller may control the switches within the SIMO converter 104 to supply the switching output voltage according to the peak current reference. The SIMO converter 104 supplies the switching output voltage to the electronic device when the peak current reference is reached during the inductor energization phase.

[0343] Further requirements for voltage stability: Advantages in DCM VNA: Peak current reference for each output is provided

[0344] FIG. 39 illustratively shows a block diagram of a SIMO system according to some embodiments that may include an input terminal 102, a SIMO 104, regulators 106a-n, and output voltages 108a-n as described above. The SIMO system 3900 may also include a switch controller 3902.

[0345] In FIG. 39, a plurality of regulators 106a-n and one switch controller 3902 are shown. In some embodiments of the present disclosure, the regulators 106a-n may be electrically coupled to different output portions of the SIMO 104 as described above. For example, the system 3900 may include two regulators 106a-n that are electrically coupled to different output portions of the SIMO 104. In some embodiments of the present disclosure, the system 3900 may include one regulator 106 and one switch controller 3902. In other embodiments of the present disclosure, the system 3900 may include a plurality of regulators 106a-n and a plurality of switch controllers 3902 or one switch controller 3902. It should be understood that the various elements shown within the regulators 106a-n may be located within the switch controller 3902.

[0346] Regulator 106 may include an amplifier circuit 3908 electrically coupled to the output of SIMO 104. The amplifier circuit 3908 may receive the switching output voltage 108 and the reference voltage 3906. The amplifier circuit 3908 may compare the switching output voltage 108 with the reference voltage 3906 and generate a differential analog output signal that may also be referred to as an error signal 3910. The error signal 3910 is supplied to a PI regulator 3912. It should be noted that, if necessary, the error signal 3910 may be further amplified. The regulator 106 may further include a proportional integral (PI) regulator 3912. The PI regulator 3912 may include a proportional part (not shown) and an integral part (not shown). The PI regulator 3912 may regulate the regulator-specific target output voltage of the regulator 106 to supply a compensated target output voltage reference 3914. The PI regulator 3912 may perform various functions on the error signal 3910 to generate a compensated target output voltage 3914 for each output voltage. The compensated target output voltage reference 3914 may be proportional to the error signal 3910 and may be an integral of the error signal 3910.

[0347] The switch controller 3902 may use one of the compensated target output voltages 3914 to generate a switch control signal that controls the switching from the inductor energizing phase to the inductor de-energizing phase. The switch controller 3902 may include a multiplexer 3920, a ramp comparator 3930, and a set-reset (SR) flip-flop circuit 3940. The input of the multiplexer 3920 may be electrically coupled to the outputs of regulators 106a-n. The output of the multiplexer 3920 may be electrically coupled to the input of the ramp comparator 3930. The comparator 3930 may receive the detected inductor current at the other input. Alternatively, the comparator may receive a voltage calculated from the detected inductor current. The set-reset (SR) flip-flop circuit 3940 may be electrically coupled to the output of the ramp comparator 3930.

[0348] The compensated target output voltage 3914 can be generated respectively for each of the regulators 106a to n. A plurality of compensated target output voltages 3914 can be supplied to the input section of the multiplexer 3920. The multiplexer 3920 may be a 4:1 multiplexer as shown in FIG. 39, or other multiplexer sizes such as 8:1 and 16:1 may be used. For example, the input section of the multiplexer 3920 may match the number of output sections of the SIMO104 so as to select the output voltages 108a to n. The compensated target output voltage 3914 can be generated for each of the output voltages 108a to n. The multiplexer 3920 may select one from the compensated target output voltages 3914 according to one or more selection signals. The selected compensated target output voltage 3924 among the plurality of compensated target output voltages 3914 can be supplied to the ramp comparator circuit 3930.

[0349] The switch controller 3902 can sequentially supply the compensated target output voltage 3914 to the ramp comparator circuit 3930. The ramp comparator circuit 3930 may compare the selected target output voltage 3924 with the detected inductor current ramp. Further, the comparator circuit 3930 can generate a comparison voltage 3932 based on the comparison.

[0350] The SR flip-flop circuit 3940 can receive the comparison voltage 3932 and the clock signal 3934. The SR flip-flop circuit 3940 can generate a duty cycle voltage 3948 based on the comparison voltage 3932 and the clock signal 3934. The duty cycle voltage 3948 is used in the discontinuous conduction mode (DCM) and can provide stability.

[0351] As a result, the SIMO system 3900 may be used to create a discontinuous inductor period as shown in FIG. 14. As described above, FIG. 14 shows a graphical representation 1400 of the simulation of the discontinuous inductor period according to at least one embodiment described in the present disclosure.

[0352] FIG. 40 illustratively shows a flowchart of a SIMO operation method according to some embodiments. Method 4000 includes, in a duty cycle, supplying a switching output voltage in response to an input voltage supplied to an inductor 4002; supplying a target output voltage associated with each of a plurality of converter output portions to each of the plurality of converter output portions by regulating the switching output voltage 4004; controlling a plurality of switches to control the switching output voltage 4006; selecting a converter output portion of the plurality of converter output portions to which the switching output voltage is supplied during a duty cycle of the plurality of duty cycles, each duty cycle including an inductor energizing phase and an inductor de-energizing phase 4008; and switching from an inductor energizing phase to an inductor de-energizing phase for the selected converter output portion of the plurality of converter output portions within at least one duty cycle of the plurality of duty cycles, using the progression of the inductor current 4010.

[0353] FIG. 41 illustratively shows a flowchart of a SIMO operation method according to some aspects. Method 4100 includes, in a duty cycle of a plurality of duty cycles, supplying a switching output voltage to a converter output among a plurality of converter outputs in response to an input voltage supplied to an inductor at 4102; supplying a target output voltage associated with each to each of the plurality of converter outputs by regulating the switching output voltage at 4104; controlling a plurality of switches to control the switching output voltage at 4106; applying the switching output voltage to a converter output among a plurality of converter outputs at 4108; selecting a converter output among the plurality of converter outputs to which the switching output voltage is supplied for each of the plurality of duty cycles at 4110; and switching from an inductor energizing phase to an inductor de-energizing phase based on a comparison between a target current representing a regulator-specific target output voltage associated with each and a process of an inductor current flowing through the inductor for the selected converter output among the plurality of converter outputs within at least one duty cycle of the plurality of duty cycles at 4112.

[0354] FIG. 42 shows a block diagram of an exemplary system 4200 including a SIMO converter 104 in accordance with at least one aspect described in the present disclosure. System 4200 may include a SIMO converter 104, one or more time-ON generators 4215a-e, a switch controller 4217, and a level shifter 4219.

[0355] System 4200 may include one or more switches 204. In FIG. 42, for simplicity of illustration and discussion, only one switch controller 4217 is shown and described. In some aspects of the present disclosure, system 4200 may include a plurality of switch controllers 4217. In some aspects of the present disclosure, system 4200 may include one time-ON generator 4215 electrically coupled to one or more SIMO converter outputs.

[0356] The SIMO converter 104 may correspond to the SIMO converter 104 described elsewhere in this disclosure. The SIMO converter 104 may include a plurality of output portions to supply the switching output voltage 108 at different values.

[0357] The time-ON generators 4215a to e may determine the T ON thereof. The time-ON generators 4215a to e may determine the time during which the switches 204a to n for the converter output portions are on to supply the switching output voltage at the corresponding converter output portions. For example, the time-ON generator 4215a may determine the time during which the switch 204a needs to be on to discharge the inductor and supply the switching output voltage 108 at the first converter output portion. The time-ON generators 4215a to e may generate the T ON thereof based on the corresponding peak current reference of each switching output voltage.

[0358] The switch controller 4217 may be configured to control the switches within the SIMO converter 104 to selectively apply the switching output voltage 108 to the converter output portions.

[0359] The switch controller 4217 may control the SIMO switch to generate one or more switch output voltages based on the T ON signal from the generator 4215 and the clock voltage 4230. In some aspects of this disclosure, when the inductor reaches the peak current and the clock voltage 4230 is received, the switch controller 4217 may generate a switch voltage such that the SIMO converter 104 supplies the switching output voltage according to the peak current reference.

[0360] The level shifter 4219 receives the switch voltage. The level shifter 4219 can shift one or more voltage levels of the switch voltage to a level sufficient to transition the corresponding switch in the SIMO converter 104 between an open position and a closed position. The level shifter 4219 can generate a gate voltage 4213 based on the switch voltage. In some aspects of the present disclosure, the level shifter 4219 can delay the gate voltage 4213 based on the corresponding stage of the SIMO converter 104.

[0361] For example, a linear regulator or a switched capacitor network may receive the gate voltage 4213 to supply the switching output voltages 108a - n.

[0362] FIG. 43 shows a block diagram of an exemplary system 4300 including a SIMO converter 104 in accordance with at least one aspect described in the present disclosure. The system 4300 can include a SIMO converter 104, one or more time - ON generators 4215a - e, a switch controller 4217, and a level shifter 4219.

[0363] The system 4300 may include one or more linear regulators 4306. In FIG. 43, for the sake of brevity of illustration and discussion, only one switch controller 4217 is shown and described. In some aspects of the present disclosure, the system 4300 may include multiple switch controllers 4217. In some aspects of the present disclosure, the system 4300 may include one linear regulator 4306 electrically coupled to one or more SIMO converter outputs. The linear regulator 4306 may correspond to the LDO 106 described elsewhere in the present disclosure.

[0364] The linear regulator 4306 can receive the gate voltage 4213 and regulate the switching output voltages 108a - n according to a peak - current reference.

[0365] FIG. 44 shows a block of an exemplary system 4400 that includes a SIMO converter 104, according to at least one aspect described in the present disclosure. The system 4400 may include a SIMO converter 104, one or more time-ON generators 4215a-e, a switch controller 4217, and a level shifter 4219.

[0366] The system 4400 may include a switched capacitor network 4406. In FIG. 44, for purposes of illustration and brevity of discussion, only one switch controller 4217 is shown and described. In some aspects of the present disclosure, the switched capacitor network 4406 may be electrically coupled to one or more SIMO converter outputs.

[0367] The switched capacitor network 4406 may receive a gate voltage 4213 and regulate the switching output voltages 108a-n according to a peak current reference. The switched capacitor network 4406 may include a separate switch controller (not shown) for controlling the switched capacitors. The switched capacitor network 4406 may use a filter to open and close switches based on the gate voltage 4213. The gate network 4406 of the switched capacitors may supply a regulated switching output voltage according to a peak current reference.

[0368] The switch controller may be used to control the duty cycle for each SIMO output current using the peak of the output voltage or a target current. The SR circuit may generate a duty cycle voltage using a selected target voltage reference for each SIMO output. The duty cycle voltage may be used to control one or more of the switches of the SIMO system to determine when to switch from an inductor energizing phase to an inductor de-energizing phase based on a comparison of the peak output voltage and the input voltage.

[0369] Each regulator may include a PI block for generating a peak current reference for each output voltage. Each of the reference signals may be sequentially supplied to a ramp comparator to generate each duty cycle voltage. The duty cycle voltage or duty command may be generated discontinuously to enhance the stability of the SIMO system.

[0370] The SIMO system may include a multiplexer for selecting from each of the target output voltages for each of the SIMO output voltages. The multiplexer may sequentially select the target output voltages and supply them to the ramp comparator. The ramp comparator may take two inputs such as the input voltage and the selected target output voltage to generate a comparison used to determine when the inductor switches between the energizing phase and the de-energizing phase.

[0371] For example, the switch control may switch between the inductor energizing phase and the inductor de-energizing phase when the target output voltage approaches the input voltage.

[0372] The ramp comparator may generate a comparison signal used as an input to an SR flip-flop circuit. The SR flip-flop circuit may receive a clock signal at its S input and the comparison signal from the ramp comparator at its R input. Based on these inputs, the SR flip-flop may generate a duty cycle voltage. The duty cycle voltage may be used as a switch control signal to control the switch controller to switch from the inductor energizing phase to the inductor de-energizing phase.

[0373] The elements of the SIMO system may be implemented on a common chip or as separate elements.

[0374] The SIMO converter 104 may include one or more voltage detectors, one or more current detectors, or some combination thereof. The voltage detector, the current detector, or some combination thereof may measure the current or voltage within the SIMO converter 104 at different stages of the operation of the SIMO converter 104. The SIMO converter 104 may reconstruct the actual inductance curve of the inductor 202 based on the measured current, voltage, or some combination thereof.

[0375] According to an aspect of the present disclosure, the SIMO buck - boost converter may utilize one or more measurements (e.g., one or more voltage measurements and / or one or more current measurements) to reconstruct the actual inductance curve of the inductor. The SIMO converter may use the actual inductance curve to adjust the duty cycle of the switches within the SIMO converter so as to supply a switching output voltage within the voltage domain of an electronic device coupled to the converter output.

[0376] FIG. 45 shows a block diagram of an exemplary system 4500 including a SIMO converter 104 in accordance with at least one aspect described in the present disclosure. The system 4500 may also include a first sensor 4502, a second sensor 4504, and a third sensor 4506. The SIMO converter 104 may otherwise correspond to the SIMO converter 104 described above in connection with FIG. 4.

[0377] In some aspects of the present disclosure, the first sensor 4502 may be electrically coupled between the first terminal of the inductor 202 and the switch 206. In other aspects of the present disclosure, the first sensor 4502 may be electrically coupled to the first terminal of the inductor 202. In some aspects of the present disclosure, the second sensor 4504 may be electrically coupled between the first terminal of the inductor 202 and the switch 208. In other aspects of the present disclosure, the second sensor 4504 may be electrically coupled to the first terminal of the inductor 202. In some aspects of the present disclosure, the third sensor 4506 may be electrically coupled between the second terminal of the inductor 202 and one or more of the switches 204a - n. In other aspects of the present disclosure, the third sensor 4506 may be electrically coupled to the second terminal of the inductor 202.

[0378] In some aspects, the first sensor 4502, the second sensor 4504, or the third sensor 4506 may be communicatively or electrically coupled to a controller (not shown). In some aspects of the present disclosure, the controller may be the switch controller described in the above paragraph.

[0379] In some aspects of the present disclosure, the first sensor 4502 and the second sensor 4504 may detect the voltage or current at the inductor 202. For example, the first sensor 4502 may detect the input voltage or input current at the first terminal of the inductor 202. As another example, the second sensor 4504 may detect the voltage or current at the first terminal of the inductor 202. In these and other aspects of the present disclosure, the first sensor 4502 may be configured to detect the input voltage or input current of the inductor 202 during the energization phase. The energization phase may occur such that the inductor 202 is energized (e.g., charged). For example, the controller may transition the switch to a state where the inductor 202 receives the input voltage (e.g., switches 206 and 210 are closed and switch 208 is open).

[0380] In some aspects of the present disclosure, the second sensor 4504 may be configured to detect the voltage or current at the first terminal of the inductor 202 during the discharge phase. The discharge phase may occur such that the inductor 202 is discharged (e.g., conducted by one or more of the switches 204a - n). For example, the controller may transition the switch to a state where the inductor 202 is electrically separated from the input voltage and electrically coupled to the output of the SIMO converter 104 (e.g., switches 206 and 210 are open, and one or more of switches 208 and 204a - n are closed).

[0381] In some aspects of the present disclosure, the third sensor 4506 may detect the switching output voltage or output current at the second terminal of the inductor 202. In these and other aspects of the present disclosure, the third sensor 4506 may detect the switching output voltage or output current during the energization or discharge phase.

[0382] In some aspects of the present disclosure, the system 4500 may operate to control the switching output voltage during the duty cycle of the inductor 202 (e.g., the inductor period including the energization and discharge phases). In these and other aspects of the present disclosure, the controller may determine an input voltage value, a voltage value, a switching output voltage value, an input current value, a current value, or an output current value. In some aspects of the present disclosure, the controller may determine the input voltage value, the voltage value, the switching output voltage value, the input current value, the current value, or the output current value based on the detected input voltage, voltage, switching output voltage, input current, current, or output current, respectively.

[0383] FIG. 46 shows a graphical representation 4600 of the current in the inductor during inductor periods 4610a - b, according to at least one aspect described in the present disclosure. In FIG. 46, curve 4616 represents the known inductance of the inductor with respect to the current in the inductor (e.g., inductor curve 4616). As represented by the inductor curve 4, as the current in the inductor increases, the inductance of the inductor decreases.

[0384] Curves 4611a - b may respectively represent the current in the inductor between the first inductor period 4610a and the second inductor period 4610b without any dilatation of the inductor. Curves 4614a - b may respectively represent the current in the inductor between the first inductor period 4610a and the second inductor period 4610b with dilatation of the inductor. Further, curve 4612 may represent the current in the inductor during the first inductor period 4610a with dilatation of the inductor. As represented by the differences between curves 4611a - b, 4612, and 4614a - b, there are differences in the current of the inductor between inductor periods 4610a - b. In some aspects of the present disclosure, the differences between curves 4611a - b, 4612, and 4614a - b may be due to the dilatation of inductance when the current increases.

[0385] FIG. 47 shows a graphical representation 4700 of the current in the inductor between inductor periods 4610a - b and the known inductance rating relative to the interpolated actual inductance rating, according to at least one aspect described in the present disclosure.

[0386] In some aspects of the present disclosure, the interpolated actual inductance rating 4709 may be interpolated using the input voltage value, input current value, or switching output voltage value of the inductor, as explained elsewhere in the present disclosure. Current 4614a may be divided into a plurality of portions represented as d i1 , d i2 , d i3 , and d i4 in FIG. 47. Each portion d i1 , d i2 , d i3 , and d i4 of the measured current 4616a may correspond to different portions of the interpolated inductor curve 4709. For example, portion d i4 may correspond to the first portion 4708a, portion d i3 may correspond to the second portion 4708b, portion d i2 may correspond to the third portion 4708c, portion di1 may correspond to the fourth part 4708d. In some aspects of the present disclosure, each part 4708a - d of the interpolated inductor curve 4709 corresponds to the corresponding part d of the measured current 4616a i1 d i2 d i3 and d i4 and may be interpolated based on d. In other aspects of the present disclosure, each part 4708a - d of the interpolated inductor curve 4709 corresponds to different parts d of the measured current 4616a i1 d i2 d i3 and d i4 and may also correspond to d.

[0387] FIG. 48 shows a flowchart of an exemplary method 4800 for operating a switched converter in accordance with at least one aspect described in the present disclosure. Method 4800 may include one or more blocks 4802, 4804, 4806, 4808, or 4810. Although shown as separate blocks, the operations associated with one or more of the blocks of method 4800 may, depending on a particular implementation, be further divided into additional blocks, combined into fewer blocks, or removed.

[0388] At block 4802, the switch may be controlled. In some aspects of the present disclosure, the switch may be controlled to control the switching output voltage in a duty cycle. In these and other aspects of the present disclosure, each duty cycle may include an energizing phase and a de - energizing phase. During the energizing phase, a charge storage component may be energized. Further, during the de - energizing phase, the charge storage component may be de - energized to one or more of the converter output parts among the plurality of converter output parts.

[0389] In block 4804, the method may include detecting a component input voltage, a component input current, and a switching output voltage. In some aspects of the present disclosure, the method may include detecting the component input voltage and the component input current at a first node of a charge storage component. Further, in some aspects of the present disclosure, the method may include detecting the switching output voltage at a second node of the charge storage component.

[0390] In block 4806, the method may include determining a component input voltage value, a component input current value, and / or a switching output voltage value by a first sensor. In some aspects of the present disclosure, the method may include determining the component input voltage value (e.g., input voltage value) and the component input current value (e.g., input current value) at the first node of the charge storage component during the start and end of a biasing phase. Further, in some aspects of the present disclosure, the method may include determining the switching output voltage value at the second node of the charge storage component during the start and end of the biasing phase.

[0391] In block 4808, the method may include determining a component input voltage value, a component input current value, and / or a switching output voltage value by a second sensor. In some aspects of the present disclosure, the method may include determining at least one of the component input voltage value, the component input current value, or the switching output voltage value during the start or end of at least one discharging phase. The method may include determining the component input voltage value or the component input current value at the first node of the charge storage component. Further, the method may include determining the switching output voltage value at the second node of the charge storage component.

[0392] In block 4810, the method may include determining an electrical characteristic of the charge storage component. In some aspects of the present disclosure, the method may include determining the electrical characteristic based on the determined values.

[0393] Changes, additions, or omissions may be made to method 4800 without departing from the scope of the present disclosure. For example, the operations of method 4800 may be performed in a different order. Additionally, or alternatively, two or more operations may be performed simultaneously. Further, the operations and actions described are provided as examples only, and some of the operations and actions may be optional, consolidated into fewer operations and actions, or extended with additional operations and actions, without departing from the essence of the described aspects.

[0394] In some aspects of the present disclosure, the first sensor may be configured as a voltage sensor. In other aspects of the present disclosure, the first sensor may be configured as a current sensor. Alternatively, in some aspects of the present disclosure, the first sensor may be configured as both a voltage sensor and a current sensor.

[0395] In some aspects of the present disclosure, the second sensor may be configured as a voltage sensor. In other aspects of the present disclosure, the second sensor may be configured as a current sensor. Alternatively, in some aspects of the present disclosure, the second sensor may be configured as both a voltage sensor and a current sensor.

[0396] In some aspects of the present disclosure, the third sensor may be configured as a voltage sensor. In other aspects of the present disclosure, the third sensor may be configured as a current sensor. Alternatively, in some aspects of the present disclosure, the third sensor may be configured as both a voltage sensor and a current sensor.

[0397] In some aspects of the present disclosure, the controller may include one or more processors configured to perform various functions using a determined voltage value (e.g., a component input voltage value, a component voltage value, or a voltage value) or a determined current value (e.g., a component input current value, a component current value, or a current value) of the first or second terminal of the inductor.

[0398] In some aspects of the present disclosure, the first sensor may detect the input voltage or input current of the first terminal during the energization phase. The controller may determine the input voltage value of the first terminal of the inductor during the energization phase. In some aspects of the present disclosure, the controller may determine the input voltage value during the energization phase based on the input voltage detected by the first sensor. The controller may also determine the input current value of the first terminal during the energization phase. In some aspects of the present disclosure, the controller may determine the input current value during the energization phase based on the input current detected by the first sensor.

[0399] In some aspects of the present disclosure, the second sensor may detect the input voltage or input current of the first terminal during the de-energization phase. The controller may determine the voltage value of the first terminal of the inductor during the de-energization phase. In some aspects of the present disclosure, the controller may determine the voltage value during the de-energization phase based on the voltage detected by the second sensor. The controller may also determine the input current value of the first terminal during the de-energization phase. In some aspects of the present disclosure, the controller may determine the input current value during the de-energization phase based on the input current detected by the first sensor.

[0400] In some aspects of the present disclosure, the third sensor may detect the switching output voltage or output current of the second terminal during the energization or de-energization phase. The controller may determine the switching output voltage value of the second terminal of the inductor during the energization or de-energization phase. In some aspects of the present disclosure, the controller may determine the switching output voltage value during the energization or de-energization phase based on the switching output voltage detected by the third sensor. The controller may also determine the output current value of the second terminal during the energization or de-energization phase. In some aspects of the present disclosure, the controller may determine the output current value during the energization or de-energization phase based on the output current detected by the first sensor.

[0401] In some aspects of the present disclosure, the first sensor may detect the input voltage at the first terminal of the inductor during the start of the energization phase (e.g., at the start). In these and other aspects of the present disclosure, the start of the energization phase may correspond to a period after the switch has transitioned to a state configured to energize (e.g., charge) the inductor. In these and other aspects of the present disclosure, the controller may determine the input voltage value at the first terminal of the inductor at the start of the energization phase based on the detected input voltage.

[0402] In some aspects of the present disclosure, the first sensor may detect the input current at the first terminal of the inductor during the start of the energization phase. In these and other aspects of the present disclosure, the controller may determine the input current value at the first terminal of the inductor at the start of the energization phase based on the detected input current.

[0403] In some aspects of the present disclosure, the third sensor may detect the switching output voltage at the second terminal of the inductor during the start of the energization phase. In these and other aspects of the present disclosure, the controller may determine the switching output voltage value at the second terminal of the inductor at the start of the energization phase based on the detected switching output voltage.

[0404] In some aspects of the present disclosure, the third sensor may detect the output current at the second terminal of the inductor during the start of the energization phase. In these and other aspects of the present disclosure, the controller may determine the output current value at the second terminal of the inductor at the start of the energization phase based on the detected output current.

[0405] In some aspects of the present disclosure, the first sensor may detect the input voltage at the first terminal of the inductor during the end of the energization phase (e.g., at the end). In these and other aspects of the present disclosure, the end of the energization phase may correspond to a period before the switch transitions to a state configured to de-energize the inductor (e.g., conduct the inductor). In these and other aspects of the present disclosure, the controller may determine the input voltage value at the first terminal of the inductor during the end of the energization phase based on the detected input voltage.

[0406] In some aspects of the present disclosure, the first sensor may detect the input current at the first terminal of the inductor during the end of the energization phase. In these and other aspects of the present disclosure, the controller may determine the input current value at the first terminal of the inductor during the end of the energization phase based on the detected input current.

[0407] In some aspects of the present disclosure, the third sensor may detect the switching output voltage at the second terminal of the inductor during the end of the energization phase. In these and other aspects of the present disclosure, the controller may determine the switching output voltage value at the second terminal of the inductor during the end of the energization phase based on the detected switching output voltage.

[0408] In some aspects of the present disclosure, the third sensor may detect the output current at the second terminal of the inductor during the end of the energization phase. In these and other aspects of the present disclosure, the controller may determine the output current value at the second terminal of the inductor during the end of the energization phase based on the detected output current.

[0409] In some aspects of the present disclosure, the second sensor may detect the voltage at the first terminal of the inductor during the start of the de-energization phase (e.g., at the start). In these and other aspects of the present disclosure, the start of the de-energization phase may correspond to the period after the switch is configured to de-energize the inductor (e.g., conduct the inductor). In these and other aspects of the present disclosure, the controller may determine the voltage value at the first terminal of the inductor during the start of the de-energization phase based on the detected voltage.

[0410] In some aspects of the present disclosure, the first sensor may detect the current at the first terminal of the inductor during the start of the de-energization phase. In these and other aspects of the present disclosure, the controller may determine the current value at the first terminal of the inductor during the start of the de-energization phase based on the detected current.

[0411] In some aspects of the present disclosure, the third sensor may detect the switching output voltage of the second terminal of the inductor during the start of the discharge phase. In these and other aspects of the present disclosure, the controller may determine the switching output voltage value of the second terminal of the inductor at the start of the discharge phase based on the detected switching output voltage.

[0412] In some aspects of the present disclosure, the third sensor may detect the output current of the second terminal of the inductor during the start of the discharge phase. In these and other aspects of the present disclosure, the controller may determine the output current value of the second terminal of the inductor at the start of the discharge phase based on the detected output current.

[0413] In some aspects of the present disclosure, the second sensor may detect the voltage of the first terminal of the inductor during the end of the discharge phase (e.g., at the end). In these and other aspects of the present disclosure, the end of the discharge phase may correspond to the period before the switch moves to a state configured to energize (e.g., charge) the inductor or to a state where substantially no current appears in the inductor. In these and other aspects of the present disclosure, the controller may determine the input voltage value of the first terminal of the inductor during the end of the discharge phase based on the detected voltage.

[0414] In some aspects of the present disclosure, the second sensor may detect the current of the first terminal of the inductor during the end of the discharge phase. In these and other aspects of the present disclosure, the controller may determine the current value of the first terminal of the inductor during the end of the discharge phase based on the detected current.

[0415] In some aspects of the present disclosure, the third sensor may detect the switching output voltage of the second terminal of the inductor during the end of the discharge phase. In these and other aspects of the present disclosure, the controller may determine the switching output voltage value of the second terminal of the inductor during the end of the discharge phase based on the detected switching output voltage.

[0416] In some aspects of the present disclosure, the third sensor may detect the output current of the second terminal of the inductor during the end of the discharge phase. In these and other aspects of the present disclosure, the controller may determine the output current value of the second terminal of the inductor during the end of the discharge phase based on the detected output current.

[0417] In some aspects of the present disclosure, the controller may determine at least one of the voltage value (e.g., input voltage value or voltage value) or current value (e.g., input current value or current value) of the first terminal (e.g., first node) of the inductor (e.g., charge storage component) and the switching output voltage value between the start and end of the energization phase. In these and other aspects of the present disclosure, the controller may determine at least one of the voltage value (e.g., input voltage value or voltage value) of the first terminal of the inductor, the current value (e.g., input current value or current value) of the first terminal, or the switching output voltage value of the second terminal (e.g., second node) during the start or end of the energization phase.

[0418] In some aspects of the present disclosure, the controller may determine the electrical characteristics of the inductor (e.g., charge storage component) using the determined values. In these and other aspects of the present disclosure, the controller may determine the actual inductance value of the inductor using the input voltage value, input current value, voltage value, current value, switching output voltage value, output current value, or some combination thereof. Further, the controller may determine the electrical characteristics of the inductor by interpolating the input voltage value, input current value, voltage value, current value, switching output voltage value, output current value, or some combination thereof.

[0419] In some aspects of the present disclosure, the controller may determine the actual inductance rating (e.g., inductance curve) of the inductor based on an interpolation of an input voltage value, an input current value, a voltage value, a current value, a switching output voltage value, an output current value, or some combination thereof. In these and other examples, the controller may interpolate the actual inductance rating of the inductor based on an input voltage value, an input current value, a voltage value, a current value, a switching output voltage value, an output current value, or some combination thereof.

[0420] The controller may determine the electrical characteristics of the inductor (e.g., the voltage across the inductor u(t)) according to the following equation:

number

[0421] In equation (3), V(Lx) denotes the voltage value at the first terminal of the inductor (for example, when the SIMO converter operates in DCM mode, it is usually approximately 0 V at the beginning and end of all phases of SIMO switching, when no current flows through the inductor); - VoN denotes the respective output voltage at the converter output (or converter output rail); - L denotes the inductivity of the inductor; -i N denotes the current in the inductor during the deactivation period of each of the converter outputs N; -i N-1 is during the deactivation period of each of the converter outputs N-1 (for example, during the deactivation period immediately before the deactivation period of the converter output N). That is, i N The deactivation period of i N-1 There are no other de-energized periods between the de-energized periods of (i.e., there is exactly one energized period). -t oN denotes the duration of the deactivation period of converter output N.

[0422] In some aspects of the present disclosure, the controller may control the switch according to the electrical characteristics of the inductor. In these and other aspects of the present disclosure, the controller may control the switch to compensate for the dilating of the inductor due to the increase in the current of the inductor. For example, the controller may control the switch to increase or decrease the duty cycle of the switch.

[0423] In some aspects of the present disclosure, the controller may control the switch according to DCM. In these and other aspects of the present disclosure, when the electrical characteristics are determined such that making the inductor period discontinuous improves the performance of the SIMO converter, the controller may operate the switch according to DCM.

[0424] In some aspects of the present disclosure, the inductor may be replaced with a capacitor, and the various operations described in the present disclosure may be performed using the capacitor instead of the inductor. In these and other aspects of the present disclosure, the electrical characteristics of the capacitor may include the capacitance of the capacitor.

[0425] In some aspects, a fourth switch may be electrically coupled between the second terminal of the inductor and the switching output voltage. In these and other aspects of the present disclosure, a fifth switch may be electrically coupled between the second terminal of the inductor and the input voltage.

[0426] One or more aspects described in the present disclosure may minimize timing errors that may reduce the efficiency of the SIMO converter. Further, one or more aspects described in the present disclosure may adapt the timing (e.g., adapt the duty cycle of the switch) to compensate for over-inductive dilation under a defined load. These aspects of the present disclosure may replace an external inductor with an inductor having known inductor curve characteristics.

[0427] In some aspects of the present disclosure, the functions described with respect to the SIMO converter may be implemented by a SISO converter using oversampling.

[0428] According to one or more aspects of the present disclosure, the controller may control the switch such that the voltage ripple of the switching output voltage value is reduced. Further, according to one or more aspects of the present disclosure, the controller may control the switch based on the determined electrical characteristics so as to reduce or eliminate inaccuracies associated with control feedback calculations or timing errors.

[0429] The SIMO converter 104 may recycle the power stored in one or more of the output capacitors. The SIMO converter 104 may recycle power to the holding capacitor. The power stored in the holding capacitor may be used to charge the inductor 202 during a subsequent inductance period. Alternatively, the SIMO converter 104 may recycle power to charge the inductor 202 during a subsequent inductance period.

[0430] According to an aspect of the present disclosure, the SIMO converter may be configured to recycle unused power using one or more power holding devices (e.g., one or more capacitors). That is, unused residual charge within the SIMO converter may be collected and stored and then used as an additional energy source. Thereby, the energy efficiency of the circuit may be improved. In other words, since many electrical components have similar voltage requirements (e.g., voltage domains), unused power for one component may be temporarily stored and then redirected to other components. For example, a BLE device and a Wi-Fi device have similar voltage regions, which allows unused voltage for the converter output connected to the BLE device to be stored in a capacitor for the converter output connected to the Wi-Fi module. Further, even if components have different voltage requirements, it may be possible to power the second component with the stored voltage from the first component.

[0431] FIG. 49 shows a block diagram of an exemplary system 4900 that includes a SIMO converter 104, in accordance with at least one aspect described in the present disclosure. In some aspects of the present disclosure, the SIMO 104 may correspond to the SIMO converter 104 described elsewhere in the present disclosure. In some aspects of the present disclosure, the system 4900 may include a plurality of converter output sections that supply switching output voltages 108a - n at different values at two or more converter output sections. In some aspects of the present disclosure, the system 4900 may include one or more LDOs (not shown). In some aspects of the present disclosure, the LDO may correspond to the LDO 106 described elsewhere in the present disclosure.

[0432] The system 4900 may be configured to recycle the voltage stored in one or more of the output capacitors 4907a - n during a discharge period. In some aspects of the present disclosure, the voltage stored in one or more of the capacitors 4907a - n may be recycled to be used during a subsequent inductance period. In these and other aspects of the present disclosure, a switch controller (not shown) may control switches 204a - n, 210, 206, 208 such that the voltage stored in the capacitors 4907a - n is transferred to other components within the system 4900 during the discharge period.

[0433] In some aspects of the present disclosure, the switch controller may control switches 204a - n, 210, 206, 208 such that the voltage stored in one or more of the output capacitors 4907a - n is used to charge the inductor 202 during the discharge period. During the discharge period, in these and other aspects of the present disclosure, the switch controller may control switches 204a - n, 210, 206, 208 such that current (represented by arrow 4901 in FIG. 49) can propagate from the output capacitor (illustrated as capacitor 4907c) to the reference potential. In these and other aspects of the present disclosure, the current propagating from the output capacitor 4907c to the reference potential may store the current in the inductor 202.

[0434] In some aspects of the present disclosure, the switch controller may control switches 204a - n, 210, 206, 208 such that during the discharge period, the voltage stored in the output capacitor 4907c is transferred to a holding capacitor (not shown). In some aspects of the present disclosure, the holding capacitor may be electrically coupled to the input terminal 102 of the SIMO104. In these and other aspects of the present disclosure, the holding capacitor may be electrically coupled to the input terminal 102 via a switch (not shown).

[0435] During the discharge period, in some aspects of the present disclosure, the switch controller may control switches 204a - n, 210, 206, 208 such that current (represented by arrow 4903 in FIG. 49) can propagate from the output capacitor (illustrated as capacitor 4907c in FIG. 49) to the input terminal 102. In these and other aspects of the present disclosure, the current propagating from the output capacitor 4907c to the input terminal 102 can cause the current to be stored in the inductor 202 or the voltage to be stored in a holding capacitor electrically coupled to the input terminal 102. During a subsequent inductance cycle, the voltage stored in the holding capacitor can supply at least a portion of the input voltage.

[0436] FIG. 50 shows a graphical representation 5000 of a simulation in which an inductor is electrically coupled to a single electrical device or an output capacitor is discharged during a separate inductance cycle, in accordance with at least one aspect described in the present disclosure. In FIG. 50, waveforms 5002a - d represent the current in the inductor during the inductance cycle. Waveforms 5002a - d show how the current in the inductor changes over time during the inductance cycle. One or more of the inductance cycles can include a charging portion, a conducting portion, or a discharging portion. The charging portion is represented as portions 5004a - c in FIG. 50. The conducting portions are represented as portions 5006, 5008, 5010 in FIG. 50. The discharging portion is represented as portion 5009 in FIG. 50.

[0437] The charging portions 5004a - c show the change in current in the inductor due to the inductor being charged using the input voltage. In some aspects of the present disclosure, the inductor may be charged using the input voltage as a positive voltage. For example, the charging portions 5004a - c shown in FIG. 50 show the increase in current in the inductor due to the inductor being charged using the input voltage or the voltage stored in the recycled holding capacitor.

[0438] In some aspects of the present disclosure, the inductor may be charged using the voltage stored in the output capacitor of the system. For example, the discharging portion 5009 shows the charging (in the negative direction) of the current in the inductor due to the output capacitor discharging during the corresponding inductor period 5002c. The current in the inductor can increase in the negative direction because, during the corresponding discharging portion 5009, the current due to the voltage stored in the output capacitor flows in the opposite direction to the current due to the input voltage.

[0439] In some aspects of the present disclosure, the discharging portion 5009 may also show a decrease in the current in the inductor when the stored voltage in the output capacitor reaches a threshold as the stored voltage in the output capacitor decreases. In these and other aspects of the present disclosure, as current propagates through the inductor during the discharging portion 5009, the voltage stored in the output capacitor can decrease. When a threshold amount (e.g., approximately half) of the stored voltage is dissipated, the current in the inductor can begin to decrease due to the decrease in the stored voltage.

[0440] The conducting portions 5006, 5008, 5010 indicate a decrease in current in the inductor due to the inductor being disconnected from the input voltage and electrically coupled to an electrical device via the converter output of the SIMO converter between the conducting portions 5006, 5008, 5010. For example, in some aspects of the present disclosure, each of the conducting portions 5006, 5008, 5010 may correspond to the inductor being electrically coupled to different electronic devices via different converter outputs of the SIMO converter. As another example, in some aspects of the present disclosure, each of the conducting portions 5006, 5008, 5010 may also correspond to the inductor being electrically coupled to the same electronic device via a certain converter output of the SIMO converter.

[0441] FIG. 51 shows a flowchart of an exemplary method 5100 for operating a switched power converter in accordance with at least one aspect described in the present disclosure. The method 5100 may include one or more blocks 5102, 5104, 5106, or 5108. Although shown as separate blocks, the operations associated with one or more of the blocks of the method 5100 may be divided into additional blocks, combined into fewer blocks, or omitted, depending on a particular implementation.

[0442] In block 5102, the switch may be controlled. In some aspects of the present disclosure, the switch may be controlled to supply a switching output voltage to the converter output. In these and other aspects of the present disclosure, the switching output voltage may be supplied to the converter output in response to an input voltage supplied to the inductor.

[0443] In block 5104, the method may include energizing the inductor. In some aspects of the present disclosure, the method may also include energizing the inductor during an inductor energization period.

[0444] In block 5106, the method may include de-energizing the inductor. In some aspects of the present disclosure, the method may also include de-energizing the inductor during a de-energization period.

[0445] In block 5108, the method may include discharging a capacitor. In some aspects of the present disclosure, the capacitor may be coupled to the converter output. In these and other aspects of the present disclosure, the capacitor may include an output capacitor. Further, in some aspects of the present disclosure, the capacitor may be discharged during a discharge period. In these and other aspects of the present disclosure, the discharge period may occur outside of the inductor energization period or the inductor de-energization period. Further, in some aspects of the present disclosure, the capacitor may be discharged to store the discharged energy in an energy storage device. The energy storage device may be located inside or outside of the SIMO converter. In various aspects, the energy storage device may be a capacitor of a converter output that is not currently in use. In various aspects, the energy storage device may be an additional capacitor disposed upstream of the inductor 202. In various aspects, the energy storage device may be an additional capacitor disposed downstream of the inductor 202. In various aspects, the energy storage device may be an additional capacitor connected to a tap terminal of the inductor that can be selectively coupled to the inductor between two inductor terminals at each end region of the inductor 202.

[0446] Modifications, additions, or omissions may be made to method 5100 without departing from the scope of the present disclosure. For example, the operations of method 5100 may be performed in a different order. Additionally, or alternatively, two or more operations may be performed simultaneously. Further, the operations and actions described are given by way of example only, and some of the operations and actions may be optional, may be combined into fewer operations and actions, or may be extended to additional operations and actions, without departing from the essence of the described aspects.

[0447] FIG. 52 shows a block diagram of another exemplary system 5200 that includes a SIMO converter 104, in accordance with at least one aspect described in the present disclosure. In some aspects of the present disclosure, the SIMO converter 104 may correspond to the SIMO converter 104 described elsewhere in the present disclosure. In some aspects of the present disclosure, the system 5200 may include one or more LDOs (not shown). In some aspects of the present disclosure, the LDO may correspond to the LDO 106 described elsewhere in the present disclosure.

[0448] The system 5200 may be configured to recycle the voltage stored in one or more of the output capacitors 4907a - n during a discharge period. In some aspects of the present disclosure, the voltage stored in one or more of the output capacitors 4907a - n may be recycled for use during a subsequent inductor cycle. The voltage stored in one or more of the output capacitors 4907a - n may be recycled from one or more of the output capacitors 4907a - n to an auxiliary capacitor 5207.

[0449] A switch controller (not shown) may control an auxiliary switch 5205 to electrically couple the auxiliary capacitor 5207 to the first terminal of the inductor 202 during a discharge portion. The switch controller may control switches 204a - n, 210, 206, 208, the auxiliary switch 5205, or some combination thereof, such that the voltage stored in one or more of the output capacitors 4907a - n is transferred to the auxiliary capacitor 5207 during a discharge period.

[0450] Furthermore, during the discharge period, the switch controller may control switches 204a-n, 210, 206, 208 such that at least a portion of the voltage stored in one or more output capacitors 4907a-n is used to charge inductor 202. During the discharge period, the switch controller may control switches 204a-n, 210, 206, 208 such that current (represented by arrow 5201 in FIG. 52) can propagate from the output capacitor (represented as capacitor 4907c in FIG. 52) to the reference potential. In these and other aspects of the present disclosure, as current propagates from output capacitor 4907c to the reference potential, the current will be stored in inductor 202.

[0451] In some aspects of the present disclosure, during the discharge period, the switch controller may control switches 204a-n, 210, 206, 208, auxiliary switch 5205, or some combination thereof such that the voltage stored in output capacitor 4907c is transferred to auxiliary capacitor 5207 (e.g., a holding capacitor). During the discharge period, the switch controller may control switches 204a-n, 210, 206, 208, auxiliary switch 5205, or some combination thereof such that current (represented by arrow 5203 in FIG. 52) can propagate from the output capacitor (represented as capacitor 4907c in FIG. 52) to auxiliary capacitor 5207.

[0452] System 5200 may use inductor 202 to recycle the power stored in output capacitor 4907 to auxiliary capacitor 5207. Further, auxiliary capacitor 5207 may be implemented as a decoupling capacitor that is decoupled from inductor 202 or switch 204 by auxiliary switch 5205.

[0453] FIG. 53 shows a block diagram of another exemplary system 5300 that includes a SIMO converter 104, according to at least one aspect described in the present disclosure. In some aspects of the present disclosure, the SIMO converter 104 may correspond to the SIMO converter 104 described elsewhere in the present disclosure. The system 5300 may include one or more LDOs (not shown). The LDO() may correspond to the LDO 106 described elsewhere in the present disclosure.

[0454] The system 5300 may include a switched capacitor network 5309 (also referred to as the switch network 5309). The switched capacitor network 5309 may include auxiliary switches 5205a-d and an auxiliary capacitor 5207. The switched capacitor network 5309 may be configured to recycle the voltage stored in one or more of the output capacitors 4907a-n to the auxiliary capacitor 5207 during a discharge period.

[0455] A switch controller (not shown) may control switches 204a-n, 210, 206, 208, auxiliary switches 5205a-d, or some combination thereof, such that the voltage stored in one or more of the output capacitors 4907a-n is transferred to the auxiliary capacitor 5207 during the discharge period.

[0456] The system 5300 may not use the inductor 202 to recycle the power stored in the output capacitor 4907.

[0457] FIG. 54 shows a flowchart of an exemplary method 5400 for operating a SIMO converter, according to at least one aspect described in the present disclosure. The method 5400 may include one or more blocks 5402 through 5414. Although shown as separate blocks, the operations associated with one or more of the blocks of the method 5400 may be divided into additional blocks, combined into fewer blocks, or removed, depending on a particular implementation.

[0458] Method 5400 may include, at block 5402, starting the operation of a clock. In some aspects of the present disclosure, the clock may include a clock signal that operates a SIMO converter, a switch controller, or some combination thereof. After block 5402, block 5404 may follow.

[0459] Method 5400 may include, at block 5404, operating a SIMO converter. In some aspects of the present disclosure, the switch controller may control switches, auxiliary switches, or some combination thereof within the SIMO converter. After block 5404, block 5406 may follow.

[0460] Method 5400 may include, at block 5406, determining whether all values of a switching output voltage are high. In some aspects of the present disclosure, the switch controller may determine whether all values of the switching output voltage (e.g., the values of the switching output voltage at the corresponding converter output) are high. The switch controller may determine that the value of the switching output voltage is high when the value of the switching output voltage exceeds a threshold. In some aspects of the present disclosure, the threshold for the value of the switching output voltage may include from 1.7V to 7V, such as from 3V to 5V. If all values of the switching output voltage are high, block 5408 may follow after block 5406. If not all values of the switching output voltage are high, block 5404 may follow after block 5406. Blocks 5404 and 5460 may be repeated until all values of the switching output voltage are high.

[0461] Method 5400 may include, at block 5408, indicating that the switching output voltage should be turned off. In some aspects of the present disclosure, the switch controller may determine that the supply of the switching output voltage to the corresponding converter output should be stopped. After block 5408, block 5410 may follow.

[0462] Method 5400 may include, at block 5410, determining that the power in the output capacitor should be recycled. In some aspects of the present disclosure, the switch controller may determine whether the power in one or more output capacitors should be recycled to an auxiliary capacitor. If the power in one or more output capacitors should be recycled, block 5412 may follow block 5410. If the power in one or more output capacitors should not be recycled, block 5414 may follow block 5410.

[0463] Method 5400 may include, at block 5412, recycling the power in the output capacitor to an auxiliary capacitor. In some aspects of the present disclosure, the switch controller may control a switch, an auxiliary switch, or some combination thereof within the SIMO converter to transfer the power in the output capacitor to the auxiliary capacitor.

[0464] Method 5400 may include, at block 5414, discharging the power in the output capacitor to a reference potential. In some aspects of the present disclosure, the switch controller may control a switch, an auxiliary switch, or some combination thereof within the SIMO converter to discharge the power in the output capacitor to a reference potential (e.g., ground potential).

[0465] In some aspects of the present disclosure, the output capacitor of the SIMO converter may be used to smooth the switching output voltage (e.g., to reduce the ripple of the switching output voltage). The output capacitor may store voltage when the switching output voltage is supplied to the corresponding converter output. The output capacitor may store voltage outside the charging period or conduction period of the SIMO converter. In some aspects of the present disclosure, the voltage stored in the output capacitor may be discharged (or discarded) to a reference potential (e.g., ground) outside the corresponding inductor period. In other aspects of the present disclosure, the voltage stored in the output capacitor may be recycled for use in charging the inductor in a subsequent inductor period. In other aspects of the present disclosure, the voltage stored in the output capacitor may be used to charge the inductor for use in a subsequent inductor period.

[0466] In some aspects of the present disclosure, the power stored in the output capacitor (e.g., the energy or potential stored in the output capacitor) may be recycled and stored in a holding capacitor. In these and other aspects of the present disclosure, the holding capacitor may be selectively electrically coupled to the input of the SIMO converter. Further, in these and other aspects of the present disclosure, the switch controller may control the switch to selectively electrically couple the holding capacitor to the input of the SIMO converter.

[0467] In some aspects of the present disclosure, during the discharge period, the switches in the SIMO converter may be controlled such that current flows from one or more of the output capacitors to the holding capacitor to store voltage in the holding capacitor. In other aspects of the present disclosure, during the discharge period, the switches may be controlled such that current flows from one or more of the output capacitors to the reference potential to charge the inductor.

[0468] In some aspects of the present disclosure, the discharge period can occur outside of the inductor energization period (e.g., charging portion) or the inductor de-energization period (e.g., conduction portion). In some aspects of the present disclosure, for example, the rails of a SIMO converter (i.e., the recovery discharge path) through which charge is transferred from a holding capacitor such that the charge is discharged to an energy storage device are substantially electrically isolated from the rails involved in energizing or de-energizing the inductor during the inductor energization period or the inductor de-energization period. In such a case, the discharge period may occur partially within the inductor energization period (e.g., charging portion) or the inductor de-energization period (e.g., conduction portion).

[0469] In some aspects of the present disclosure, a single output capacitor can be discharged during the discharge period. In other aspects of the present disclosure, multiple output capacitors may be discharged during the discharge period. In these and other aspects of the present disclosure, a single output capacitor may be discharged for each discharge period. In other aspects of the present disclosure, multiple output capacitors may be discharged for each discharge period.

[0470] In some aspects of the present disclosure, the switch may be controlled such that the voltage stored in one or more output capacitors is recycled to a different output capacitor. In these and other aspects of the present disclosure, recycling the stored voltage to a different output capacitor can reduce the amount of time for the switched output voltage to stabilize during a subsequent discharge period.

[0471] In some aspects of the present disclosure, the switch controller may determine whether the charge state of one or more output capacitors satisfies a predefined criterion. In these and other aspects of the present disclosure, the switch controller may control the switch such that a discharge portion occurs when one or more output capacitors satisfy a predefined criterion. In some aspects of the present disclosure, the predefined criterion may include that the amount of voltage (e.g., energy) stored in one or more capacitors is greater than or equal to a predefined energy threshold.

[0472] In some aspects of the present disclosure, one or more of the switches may include power switches.

[0473] In some aspects of the present disclosure, the system may include a converter other than the SIMO converter, and a system with different converters may recycle the power stored in one or more output capacitors in the same or similar manner as described above.

[0474] In some aspects of the present disclosure, the power stored in the output capacitor may be recycled to multiple locations. In these and other aspects of the present disclosure, a portion of the power stored in the output capacitor may be recycled to a holding capacitor, and another portion may be recycled to an inductor.

[0475] In some aspects of the present disclosure, the power stored in the output capacitor may be recycled to another output capacitor.

[0476] The SIMO converter may supply the switching output voltage at different levels to a high-bandwidth WiFi chain and a composite chain including a Bluetooth® transmitter chain and a low-bandwidth WiFi chain at different converter output portions. The SIMO converter supplying the switching output voltage at different levels may enable the Bluetooth transmitter chain and the high-bandwidth WiFi chain within the composite chain to operate simultaneously. Further, the SIMO converter may adjust the voltage level of the switching output voltage to the Bluetooth transmitter chain and the high-bandwidth chain so as to reduce the power consumption of the Bluetooth chain while maintaining proper operation of the high-bandwidth chain.

[0477] According to an aspect of the present disclosure, the SIMO converter may supply a switching output voltage within a voltage domain for a composite chain including a high-bandwidth WiFi chain, a Bluetooth transmitter chain, and a low-bandwidth WiFi chain, or a combination thereof.

[0478] FIG. 55 shows a block diagram of an exemplary wireless transmitter 5500 that includes a DC-DC converter 5502, in accordance with at least one aspect described in the present disclosure. The wireless transmitter 5500 may also include a WiFi low band (WLB) chain 5504, a Bluetooth (BT) chain 5506, and a WiFi high band (WHB) chain 5508.

[0479] In some aspects of the present disclosure, the DC-DC converter 5502 may receive a DC voltage. In these and other aspects of the present disclosure, the DC-DC converter 5502 may generate an output voltage at a different DC voltage. In these and other aspects of the present disclosure, the voltage level of the output voltage may be based on one or more settings of the WLB chain 5504, the BT chain 5506, or the WHB chain 5508.

[0480] In some aspects of the present disclosure, the WLB chain 5504, the BT chain 5506, or the WHB chain 5508 may be electrically coupled to the DC-DC converter 5502 via a single rail 5501. In these and other aspects of the present disclosure, the WLB chain 5504, the BT chain 5506, or the WHB chain 5508 may receive an output voltage from the DC-DC converter 5502 via the rail 5501.

[0481] In some aspects of the present disclosure, the WLB chain 5504 may transmit a wireless signal in accordance with a wireless local area network (WLAN) standard. In these and other aspects of the present disclosure, the WLB chain 5504 may transmit a wireless signal in the low band in accordance with the WiFi protocol.

[0482] In some aspects of the present disclosure, the WLB chain 5504 may be electrically coupled to a second rail 5503. In these and other aspects of the present disclosure, the WLB chain 5504 may receive an input voltage via the second rail 5503.

[0483] In some aspects of the present disclosure, the BT chain 5506 may transmit a BT signal. In these and other aspects of the present disclosure, the BT chain 5506 may transmit a BT wireless signal in accordance with the BT standard.

[0484] In some aspects of the present disclosure, the BT chain 5506 may be electrically coupled to the second rail 5505. In these and other aspects of the present disclosure, the BT chain 5506 may receive an input voltage via the second rail 5503.

[0485] In some aspects of the present disclosure, the WHB chain 5508 may transmit a wireless signal according to the WLAN standard. In these and other aspects of the present disclosure, the WHB chain 5508 may transmit a high-bandwidth wireless signal according to the WiFi protocol.

[0486] In some aspects of the present disclosure, the WLB chain 5504, the BT chain 5506, or the WHB chain 5508 may receive an output voltage as a transmission signal to be transmitted by the WLB chain 5504, the BT chain 5506, or the WHB chain 5508. Further, in some aspects of the present disclosure, the WLB chain 5504, the BT chain 5506, or the WHB chain 5508 may operate simultaneously using the output voltage and transmit a corresponding wireless signal.

[0487] In some aspects of the present disclosure, the DC-DC converter 5502 supplying the output voltage to the BT chain 5506 or the WHB chain 5508 via a single rail 5501 may cause a degradation of the wireless signal. For example, the DC-DC converter 5502 supplying the output voltage to the BT chain 5506 and the WLB chain 5504 via a single rail 5501 may cause a substantial 1 dB performance degradation due to mutual loading as compared to simply the WLB chain 5504 operating using the output voltage.

[0488] In some aspects of the present disclosure, when both the BT chain 5506 and the WHB chain 5508 are transmitting using the output voltage, the DC-DC converter 5502 may supply the output voltage at a level that enables both the BT chain 5506 and the WHB chain 5508 to operate properly. Increasing the level of the output voltage based on the settings of the WHB chain 5508 when the BT chain 5506 is also transmitting may increase the power consumption by the BT chain 5506.

[0489] FIG. 56 shows a block diagram of another exemplary wireless transmitter 5600 that includes a DC-DC converter 5502, in accordance with at least one aspect described in the present disclosure. The wireless transmitter 5600 may also include a combined WLB and BT chain 5610, and / or a WHB chain 5508.

[0490] In some aspects of the present disclosure, the DC-DC converter 5502 may receive a DC voltage. In these and other aspects of the present disclosure, the DC-DC converter 5502 may generate an output voltage at a different voltage. In these and other aspects of the present disclosure, the voltage level of the output voltage may be based on one or more settings of the combined WLB and BT chain 5610 or the WHB chain 5508.

[0491] In some aspects of the present disclosure, the combined WLB and BT chain 5610 may be electrically coupled to the DC-DC converter 5502 via a rail 5605. In these and other aspects of the present disclosure, the WHB chain 5508 may be electrically coupled to the DC-DC converter 5502 via a rail 5607.

[0492] In some aspects of the present disclosure, the composite WLB and BT chain 5610 may transmit wireless signals in accordance with the WLAN standard. In these and other aspects of the present disclosure, the composite WLB and BT chain 5610 may transmit wireless signals in a low band in accordance with the WiFi protocol. In some aspects of the present disclosure, the composite WLB and BT chain 5610 may also transmit BT wireless signals. In these and other aspects of the present disclosure, the composite WLB and BT chain 5610 may transmit BT wireless signals in accordance with the BT standard.

[0493] In some aspects of the present disclosure, the composite WLB and BT chain 5610 may receive an output voltage from the DC-DC converter 5502 via the rail 5605. In these and other aspects of the present disclosure, the WHB chain 5508 may receive an output voltage from the DC-DC converter 5502 via the rail 5607.

[0494] In some aspects of the present disclosure, the composite WLB and BT chain 5610 may operate using the output voltage received via the rail 5605 and simultaneously transmit corresponding wireless signals. In these and other aspects of the present disclosure, the composite WLB and BT chain 5610 simultaneously transmitting BT wireless signals and WLB wireless signals using the output voltage as a transmission signal received via the rail 5605 (e.g., a single rail) may reduce the efficiency of the BT wireless signals. Further, in some aspects of the present disclosure, the efficiency of the BT wireless signals may be reduced by a WiFi power amplifier within the WiFi portion of the composite WLB and BT chain 5610 that includes a higher maximum power (Pmax) than the devices within the BT portion of the composite WLB and BT chain 5610.

[0495] FIG. 57 shows a block diagram of an exemplary wireless transmitter 5700 that includes a hybrid converter 5712 in accordance with at least one aspect described in the present disclosure. In some aspects of the present disclosure, the hybrid converter 5712 may correspond to the hybrid converters described elsewhere in the present disclosure. The hybrid converter 5712 may include the SIMO converters 104 and one or more LDOs 106a, b.

[0496] In some aspects of the present disclosure, the SIMO converter 104 may correspond to the SIMO converter 104 described elsewhere in the present disclosure. In these and other aspects of the present disclosure, the LDOs 106a, b may correspond to the LDO 106 described elsewhere in the present disclosure.

[0497] In some aspects of the present disclosure, the wireless transmitter 5700 may include a switch controller (not shown) configured to control the switches within the SIMO converter 104. In these and other aspects of the present disclosure, the switch controller may control the switches to selectively apply the switching output voltage to different converter output portions of the SIMO converter 104.

[0498] In some aspects of the present disclosure, the switches of the SIMO converter 104 may supply the switching output voltage as a transmission signal to one or more converter output portions during the duty cycle of the SIMO converter 104. In these and other aspects of the present disclosure, the switches of the SIMO converter 104 may supply the switching output voltages 108a - n at different values across two or more of the converter output portions. Further, in some aspects of the present disclosure, the switch controller may control the switches of the SIMO converter 104 to supply the switching output voltage in response to the input voltage supplied to the inductor.

[0499] In some aspects of the present disclosure, the switch controller may control the switches of the SIMO converter 104 to supply the switching output voltage during the duty cycle of the SIMO converter 104.

[0500] In some aspects of the present disclosure, the WHB chain 5508 may be electrically coupled...

Claims

1. An inductor, A plurality of converter output lines, A plurality of switches that supply a switching output voltage in response to an input voltage applied to the inductor according to separate inductor cycles, each of the inductor cycles including a charging portion in which the inductor receives the input voltage and is electrically coupled to one specific converter output line among the plurality of converter output lines, and a conduction portion in which the inductor is disconnected from the input voltage and is electrically coupled to a corresponding one converter output line other than the specific converter output line among the plurality of converter output lines; the plurality of switches, At least one ripple detector electrically coupled to a relevant converter output line among the plurality of converter output lines and detecting a ripple of the switching output voltage at the relevant converter output line, A switch controller configured to control the plurality of switches based on a ripple voltage corresponding to the ripple detected by the at least one ripple detector so as to control the switching output voltage, At least one regulator configured to dynamically set a predefined target output voltage specific to each relevant regulator at a relevant converter output line among the plurality of converter output lines and regulate the switching output voltage to stay within a predefined range from the target output voltage using a current from another converter output line among the plurality of converter output lines, A single inductor multiple output circuit having the same.

2. The plurality of switches include, A first switch coupled between a first terminal of the inductor and the input voltage, A second switch coupled between the first terminal of the inductor and a reference potential, The single inductor multiple output circuit according to claim 1.

3. The plurality of switches include a third switch coupled between a second terminal of the inductor and a reference potential, The single inductor multiple output circuit according to claim 1.

4. The plurality of switches include a fourth switch coupled between a second terminal of the inductor and a terminal that supplies the switching output voltage, The single inductor multiple output circuit according to claim 1.

5. ​ The plurality of switches includes a fifth switch coupled between the second terminal of the inductor and the input voltage. The single-inductor multiple-output circuit according to claim 1.

6. The at least one regulator includes a sixth switch coupled between the converter output line and another converter output line. The single-inductor multiple-output circuit according to any one of claims 1 to 5.

7. The at least one regulator includes a first comparator circuit configured to compare the switching output voltage with a predefined first threshold voltage and control the sixth switch such that the sixth switch is closed when the switching output voltage is lower than the predefined first threshold voltage and the sixth switch is open when the switching output voltage is higher than the predefined first threshold voltage. The single-inductor multiple-output circuit according to claim 6.

8. The at least one regulator includes a seventh switch coupled between the converter output line and yet another converter output line among the plurality of converter output lines. The single-inductor multiple-output circuit according to any one of claims 1 to 7.

9. The at least one regulator includes a second comparator circuit configured to compare the switching output voltage with a predefined second threshold voltage and control the seventh switch such that the seventh switch is closed when the switching output voltage is higher than the predefined second threshold voltage and the seventh switch is open when the switching output voltage is lower than the predefined second threshold voltage. The single-inductor multiple-output circuit according to claim 8.

10. A switching stage having an inductor and a plurality of switches, and in accordance with separated inductor periods, in response to an applied input voltage depending on the switching states of the plurality of switches, supplying a switching output voltage at a certain converter output line among a plurality of converter output lines, each of the inductor periods including a charging portion where the inductor receives the input voltage and is electrically coupled to a specific one of the plurality of converter output lines, and a conducting portion where the inductor is disconnected from the input voltage and is electrically coupled to a corresponding one of the plurality of converter output lines other than the specific converter output line, the switching stage; At least one ripple detector electrically coupled to a relevant converter output line among the plurality of converter output lines, detecting a ripple of the switching output voltage at the relevant converter output line, and the ripple voltage corresponding to the ripple being used for controlling the switching states of the plurality of switches; At least one regulator configured to receive the switching output voltage and dynamically set an output voltage at a first converter output line among the plurality of converter output lines, determining at least one of whether the switching output voltage exceeds a predefined upper threshold voltage greater than a target regulator output voltage or whether the switching output voltage is lower than a predefined lower threshold voltage less than the target regulator output voltage, and having a circuit configured to regulate the switching output voltage using a current from a second converter output line among the plurality of converter output lines; A single-inductor multiple-output circuit having the above.

11. The plurality of switches include a first switch coupled between a first terminal of the inductor and the input voltage; and a second switch coupled between the first terminal of the inductor and a reference potential. The single-inductor multiple-output circuit according to claim 10.

12. The single-inductor multiple-output circuit according to claim 10. The plurality of switches include a third switch coupled between a second terminal of the inductor and a reference potential. The single-inductor multiple-output circuit according to claim 10.

13. The plurality of switches includes a fourth switch coupled between the second terminal of the inductor and the terminal for supplying the switching output voltage. The single-inductor multiple-output circuit according to claim 10.

14. The plurality of switches includes a fifth switch coupled between the second terminal of the inductor and the input voltage. The single-inductor multiple-output circuit according to claim 10.

15. The at least one regulator includes a sixth switch coupled between the second converter output line and the first converter output line. The single-inductor multiple-output circuit according to claim 10.

16. The at least one regulator has a first comparator circuit configured to compare the switching output voltage with the predefined lower threshold voltage and control the sixth switch such that the sixth switch is closed when the switching output voltage is lower than the predefined lower threshold voltage and the sixth switch is open when the switching output voltage is higher than the predefined lower threshold voltage. The single-inductor multiple-output circuit according to claim 15.

17. The at least one regulator includes a seventh switch coupled between the third converter output line and the first converter output line. The single-inductor multiple-output circuit according to any one of claims 10 to 16.

18. The at least one regulator has a second comparator circuit configured to compare the switching output voltage with the predefined upper threshold voltage and control the seventh switch such that the seventh switch is closed when the switching output voltage is higher than the predefined upper threshold voltage and the seventh switch is open when the switching output voltage is lower than the predefined upper threshold voltage. The single-inductor multiple-output circuit according to claim 17.

19. A method of operating a single-inductor multiple-output (SIMO) converter, wherein the SIMO converter has a plurality of switches that supply a switched output voltage in response to an input voltage applied to an inductor, the method comprising: a first switch coupled between a first terminal of the inductor and the input voltage; a second switch coupled between the first terminal of the inductor and a reference potential; and a third switch coupled between a second terminal of the inductor and the reference potential. In the method of operation, detecting a ripple of the switched output voltage by a ripple detector; controlling the plurality of switches based on a ripple voltage corresponding to the ripple detected by the ripple detector so as to control the switched output voltage; dynamically setting a predefined target output voltage specific to each associated regulator, and operating each regulator of a plurality of regulators to regulate the switched output voltage to stay within a predefined range from the target output voltage using the input voltage and having the supplying of the switched output voltage by the plurality of switches includes the plurality of switches supplying the switched output voltage in accordance with separate inductor cycles, each of the inductor cycles including a charging portion in which the inductor receives the input voltage and is electrically coupled to a particular one of a plurality of converter output lines of the SIMO converter, and a conduction portion in which the inductor is disconnected from the input voltage and electrically coupled to a corresponding one of the plurality of converter output lines other than the particular converter output line. Method of operation. [

20. ] A method of operating a SIMO converter, comprising: Controlling a switching stage having an inductor and a plurality of switches according to separated inductor periods to supply a switched output voltage in response to an applied input voltage depending on the switching states of the plurality of switches, each of the inductor periods including a charging portion in which the inductor receives the input voltage and is electrically coupled to a specific one of a plurality of converter output lines of the SIMO converter, and a conducting portion in which the inductor is disconnected from the input voltage and is electrically coupled to a corresponding one of the plurality of converter output lines other than the specific converter output line, The switching state of the switching stage is obtained by controlling the switching stage based on a ripple voltage corresponding to the ripple of the switched output voltage detected by a ripple detector, The plurality of switches include a first switch coupled between a first terminal of the inductor and the input voltage, a second switch coupled between the first terminal of the inductor and a reference potential, and a third switch coupled between a second terminal of the inductor and the reference potential, Each of a plurality of regulators dynamically sets an output voltage in response to receiving the switched output voltage, determines at least one of whether the switched output voltage exceeds a predefined upper threshold voltage greater than a target regulator output voltage or whether the switched output voltage is less than a predefined lower threshold voltage less than the target regulator output voltage, and regulates the switched output voltage using the input voltage, Operating method.

21. An operating method of a converter, comprising: A plurality of switches supply a switching output voltage to a converter output section among a plurality of converter output sections in response to an input current supplied to an inductor according to separated inductor cycles, and each of the inductor cycles includes a charging portion in which the inductor receives the input current and is electrically coupled to a specific converter output section among the plurality of converter output sections, and a conduction portion in which the inductor is disconnected from the input current and the inductor is electrically coupled to a corresponding one of the converter output sections other than the specific converter output section among the plurality of converter output sections. Detecting a ripple of the switching output voltage in the associated converter output section by at least one ripple detector electrically coupled to the associated converter output section among the plurality of converter output sections. Controlling the plurality of switches based on a ripple voltage corresponding to the ripple detected by the at least one ripple detector so as to control the switching output voltage to apply the switching output voltage to a converter output section among the plurality of converter output sections. Dynamically setting a target output voltage specific to each associated regulator to each converter output section among the plurality of converter output sections. Selecting an operation mode of the converter from a first operation mode or a second operation mode. Operating the converter as a single inductor multiple output in the first operation mode. Operating the converter in the second operation mode such that, for at least one converter output section, the switching output voltage is not regulated, and for at least one other converter output section, the associated regulator dynamically sets a target output voltage specific to the associated regulator. An operating method having the above.

22. A computer-readable medium having instructions that, when executed, cause one or more processors to execute the operating method according to any one of claims 19 to 21.

23. An inductor, A plurality of converter output lines, A plurality of switches that supply a switching output voltage in response to an input voltage applied to the inductor according to a separated inductor period, each of the inductor periods including a charging portion in which the inductor receives the input voltage and is electrically coupled to one specific converter output line among the plurality of converter output lines, and a conduction portion in which the inductor is disconnected from the input voltage and is electrically coupled to a corresponding one converter output line other than the specific converter output line among the plurality of converter output lines; the plurality of switches, At least one ripple detector that is electrically coupled to a related converter output line among the plurality of converter output lines and detects a ripple of the switching output voltage at the related converter output line; A switch controller configured to control the plurality of switches based on a ripple voltage corresponding to the ripple detected by the at least one ripple detector so as to control the switching output voltage; At least one regulator configured to dynamically set a predefined target output voltage specific to each related regulator at a related converter output line among the plurality of converter output lines and regulate the switching output voltage to stay within a predefined range from the target output voltage using a current from another converter output line among the plurality of converter output lines; A single inductor multiple output circuit having; An electronic component coupled to a related converter output line among the plurality of converter output lines and configured to operate at the target output voltage of the related converter output line among the plurality of converter output lines; A system having.

24. The system according to claim 23, further comprising a further electronic component coupled to another converter output line among the plurality of converter output lines and configured to operate at the target output voltage of the another converter output line among the plurality of converter output lines. The system according to claim 23.

25. The electronic component is A transmitter, A receiver, A transceiver, A processor, and A memory component Selected from the group consisting of, The system according to claim 23 or 24.

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