Method and apparatus for transmitting and receiving radio signals in a communication system

Abstract

In one embodiment of a communication system, a method of operating a first communication node includes generating a first binary sequence and a second binary sequence; generating a first intermediate sequence having 2N elements based on the first and second binary sequences and a BPSK operation; generating a first signal sequence consisting of N elements based on an operation on elements of the first intermediate sequence; mapping first modulation symbols generated by modulating the first signal sequence to N subcarriers; and transmitting a first signal consisting of the mapped first modulation symbols, wherein the first and second binary sequences are generated based on a generator polynomial having a maximum degree p+1, where p is a natural number and N is a natural number. p It can be a natural number having a value of -1.

Description

[Technical Field]

[0001] The present disclosure relates to a radio signal transmission and reception technique in a communication system, and more particularly to a technique for improving the transmission and reception performance of a radio signal in a communication system. [Background technology]

[0002] With the development of information and communication technology, various wireless communication technologies have been developed. Representative wireless communication technologies include LTE (long term evolution) and NR (new radio), which are defined in the 3GPP (3rd Generation Partnership Project) standard. LTE is one of the 4th Generation (4G) wireless communication technologies, and NR may be one of the 5th Generation (5G) wireless communication technologies. Wireless communication technologies beyond 5G (e.g., 6th Generation (6G)) may be referred to as B5G (beyond 5G) wireless communication technologies.

[0003] In one embodiment of the communication system, a user can perform serving cell identification after acquiring time / frequency synchronization with the wireless network in order to connect to the network. Serving cell identification can be performed, for example, through physical cell identity (PCI) estimation using a predetermined synchronization signal. Each cell can have a different PCI and can transmit a synchronization signal including information for PCI identification (i.e., a synchronization signal indicating a PCI). For easy cell identification, the correlation characteristics between synchronization signals indicating different PCIs should be excellent, and the variability of the cross-correlation characteristics of all synchronization signal pairs should be as low as possible.

[0004] However, the number of distinguishable PCIs may be limited depending on the synchronization signal design method. To overcome this limitation and increase the number of distinguishable PCIs, one embodiment of a communication system may use a method of generating linearly distinct synchronization signals by cyclically shifting a cyclically distinct sequence. The sequence generated through this cyclic shift may not follow the correlation characteristics of the original sequence. This may result in degradation of the correlation characteristics between the generated synchronization signal pair, leading to a problem of high variability in the cross-correlation characteristics. A technology that can effectively increase the number of distinguishable PCIs while maintaining the correlation characteristics and variability of the synchronization signals may be required.

[0005] The matters described in this background art section are prepared to enhance understanding of the background of the invention, and may include matters that are not prior art already known to those having ordinary skill in the art to which this technology pertains. Summary of the Invention [Problem to be solved by the invention]

[0006] In order to achieve the above-mentioned requirements, an object of the present disclosure is to provide a signal transmission / reception method and apparatus for improving the performance of cell identification operations based on radio signals in a communication system. [Means for solving the problem]

[0007] In one embodiment of a communication system for achieving the above object, a method for operating a first communication node includes the steps of: generating first and second binary sequences consisting of 2N elements; generating a first intermediate sequence consisting of 2N elements based on the first and second binary sequences and a BPSK (Binary Phase Shift Keying) operation; generating a first signal sequence consisting of N elements based on an operation on the 2N elements constituting the first intermediate sequence; mapping first modulation symbols generated by modulating the first signal sequence to N subcarriers; and transmitting a first signal consisting of the mapped first modulation symbols, wherein the first and second binary sequences are generated based on a generator polynomial having a maximum degree (p+1) and a first identifier for the first communication node, where p is a natural number and N is a number less than or equal to (2 p It can be a natural number with a value of (-1).

[0008] The generating the first intermediate sequence may include generating first and second cyclic shift indexes based on the first identifier, applying the first cyclic shift index to the first binary sequence, applying the second cyclic shift index to the second binary sequence, performing the BPSK operation on a sum of the first and second binary sequences to which the first and second cyclic shift indexes have been applied, and obtaining the first intermediate sequence corresponding to a result of the BPSK operation.

[0009] The step of generating the first signal sequence may include the steps of multiplying a 2k-th element of the 2N elements constituting the first intermediate sequence by a first coefficient that is a real number, multiplying a 2k+1-th element of the 2N elements constituting the first intermediate sequence by a second coefficient that is a pure imaginary number, performing a sum operation on the 2k-th element multiplied by the first coefficient and the 2k+1-th element multiplied by the second coefficient, and obtaining a k-th element of the first signal sequence based on a result of the sum operation, wherein k may be an integer greater than or equal to 0 and less than N.

[0010] The generating the first signal sequence may include multiplying a 2k-th element of the 2N elements constituting the first intermediate sequence by a first coefficient that is a real number; multiplying a 2k+1-th element of the 2N elements constituting the first intermediate sequence by a second coefficient that is a pure imaginary number; performing a sum operation on the 2k-th element multiplied by the first coefficient and the 2k+1-th element multiplied by the second coefficient; performing a rotational transform operation by a first angle on a complex plane on a result of the sum operation; and obtaining a k-th element of the first signal sequence based on a result of the rotational transform operation, wherein k may be an integer greater than or equal to 0 and less than N.

[0011] The first angle may be one of π / 4, −π / 4, 3π / 4, or −3π / 4.

[0012] The first signal has up to (2N+1) 2 It can support distinct values.

[0013] In one embodiment of a communication system for achieving the above object, a method for operating a first communication node includes the steps of generating first and second binary sequences each consisting of (N / 2) elements and a third binary sequence each consisting of M elements, and synthesizing the first to third binary sequences and BPSK (Binary Phase Shift Keying) generating a first intermediate sequence consisting of (N / 2) elements based on a (N / 2) keying operation; generating first and second element groups each consisting of (N / 2) elements based on the first intermediate sequence; generating a first signal sequence consisting of N elements based on the first and second element groups; mapping first modulation symbols generated by modulating the first signal sequence to N subcarriers; and transmitting a first signal consisting of the mapped first modulation symbols, wherein the first and second binary sequences are generated based on a generator polynomial having a maximum degree (p-1), and first to third cyclic shift indexes determined based on a first identifier for the first communication node are applied to the first to third binary sequences, respectively, where p is a natural number and N is a number less than or equal to (2 p M may be a natural number having a value equal to or less than (N / 2).

[0014] The generating the first intermediate sequence may include determining the first to third cyclic shift indexes based on the first identifier, applying the first cyclic shift index to the first binary sequence, applying the second cyclic shift index to the second binary sequence, applying the third cyclic shift index to the third binary sequence, performing the BPSK operation on a sum of the first to third binary sequences to which the first to third cyclic shift indexes have been applied, and obtaining the first intermediate sequence corresponding to a result of the BPSK operation.

[0015] The step of determining the first to third cyclic shift indexes includes the steps of determining a first variable g based on the value of the first identifier, determining a second variable Ω based on the number of values ​​that the first identifier can have, and determining the first to third cyclic shift indexes based on one or more modulo operations with the first variable g, the second variable Ω, and a first reference value t, where g, Ω, and t may be natural numbers.

[0016] The second circular shift index may be determined based on t-modulo and Ω-modulo operations on the first variable g.

[0017] The first signal can support up to (M×N×N) distinct values ​​for the first identifier.

[0018] The (N / 2) elements constituting the first element group may be represented by a k-th element, and the (N / 2) elements constituting the second element group may be represented by a (N / 2+k)-th element. The generating of the first and second element groups may include obtaining the k-th element of the first element group based on the k-th element of the (N / 2) elements constituting the first intermediate sequence, and obtaining the (N / 2+k)-th element of the second element group based on the k-th element of the (N / 2) elements constituting the first intermediate sequence. The N elements constituting the first signal sequence may be configured to include the (N / 2) elements constituting the first element group and the (N / 2) elements constituting the second element group, where k may be an integer greater than or equal to 0 and less than (N / 2).

[0019] the (N / 2) elements constituting the first element group are represented by an (N / 2-1-k)th element, and the (N / 2) elements constituting the second element group are represented by an (N / 2+k)th element; generating the first and second element groups includes obtaining the (N / 2-1-k)th element of the first element group based on the kth element of the (N / 2) elements constituting the first intermediate sequence, and obtaining the (N / 2+k)th element of the second element group based on the kth element of the (N / 2) elements constituting the first intermediate sequence; and the N elements constituting the first signal sequence are configured to include the (N / 2) elements constituting the first element group and the (N / 2) elements constituting the second element group, where k is an integer greater than or equal to 0 and less than (N / 2).

[0020] The first modulation symbols mapped to the N subcarriers may have a central symmetric structure centered on a first reference subcarrier of the N subcarriers.

[0021] The first signal may have only real components in the time domain.

[0022] In one embodiment of the communication system for achieving the above object, the first communication node includes a processor, and the processor is configured to generate first and second binary sequences each consisting of (N / 2) elements and a third binary sequence consisting of M elements, and to synthesize the first to third binary sequences and BPSK (Binary Phase Shift Keying) modulation. and generating a first intermediate sequence consisting of (N / 2) elements based on a keying operation, generating first and second element groups each consisting of (N / 2) elements based on the first intermediate sequence, generating a first signal sequence consisting of N elements based on the first and second element groups, mapping first modulation symbols generated by modulating the first signal sequence to N subcarriers, and transmitting a first signal consisting of the mapped first modulation symbols, wherein the first and second binary sequences are generated based on a generator polynomial having a maximum degree (p-1), and first to third cyclic shift indexes determined based on a first identifier for the first communication node are applied to the first to third binary sequences, respectively, where p is a natural number, and N is a number less than or equal to (2 p M may be a natural number having a value equal to or less than (N / 2).

[0023] When generating the first intermediate sequence, the processor may be further operable to cause the first communication node to determine the first to third cyclic shift indexes based on the first identifier, apply the first cyclic shift index to the first binary sequence, apply the second cyclic shift index to the second binary sequence, apply the third cyclic shift index to the third binary sequence, perform the BPSK operation on a sum of the first to third binary sequences to which the first to third cyclic shift indexes have been applied, and obtain the first intermediate sequence corresponding to a result of the BPSK operation.

[0024] When determining the first to third cyclic shift indexes, the processor is further operative to cause the first communication node to determine a first variable g based on the value of the first identifier, determine a second variable Ω based on the number of values ​​that the first identifier can have, and determine the first to third cyclic shift indexes based on one or more modulo operations with the first variable g, the second variable Ω, and a first reference value t, where g, Ω, and t may be natural numbers.

[0025] The second circular shift index may be determined based on t-modulo and Ω-modulo operations on the first variable g.

[0026] The first signal can support up to (M×N×N) distinct values ​​for the first identifier. [Effects of the Invention]

[0027] According to an embodiment of a method and apparatus for transmitting and receiving a wireless signal in a communication system, the performance of an estimation operation or an identification operation based on a wireless signal transmitted and received between a transmitting node and a receiving node can be improved. The wireless signal according to an embodiment of a method and apparatus for transmitting and receiving a wireless signal in a communication system can support more identification index divisions while using the same frequency resource. The wireless signal according to an embodiment of a method and apparatus for transmitting and receiving a wireless signal in a communication system can reduce the computational complexity for an estimation operation or an identification operation. The wireless signal according to an embodiment of a method and apparatus for transmitting and receiving a wireless signal in a communication system can have lower transmission complexity while using the same frequency resource. [Brief explanation of the drawings]

[0028] [Figure 1] FIG. 1 is a conceptual diagram illustrating an embodiment of a communication system. [Figure 2] 1 is a block diagram illustrating an embodiment of a communication node that constitutes a communication system. [Figure 3]FIG. 1 is a conceptual diagram illustrating an embodiment of a radio frame structure in a communication system. [Figure 4] 1 is a flowchart illustrating an embodiment of a signal transmission and reception method in a communication system. [Figure 5a] 1 is a conceptual diagram for explaining a first embodiment of a radio signal structure in a communication system. [Figure 5b] 1 is a conceptual diagram for explaining a first embodiment of a radio signal structure in a communication system. [Figure 6a] 1 is a conceptual diagram for explaining first and second embodiments of a radio signal generation method in a communication system. [Figure 6b] 1 is a conceptual diagram for explaining first and second embodiments of a radio signal generation method in a communication system. [Figure 6c] 1 is a conceptual diagram for explaining first and second embodiments of a radio signal generation method in a communication system. [Figure 6d] 1 is a conceptual diagram for explaining first and second embodiments of a radio signal generation method in a communication system. [Figure 7a] FIG. 10 is a conceptual diagram for explaining a third embodiment of a radio signal generation method in a communication system. [Figure 7b] FIG. 10 is a conceptual diagram for explaining a third embodiment of a radio signal generation method in a communication system. [Figure 7c] FIG. 10 is a conceptual diagram for explaining a third embodiment of a radio signal generation method in a communication system. [Figure 7d] FIG. 10 is a conceptual diagram for explaining a third embodiment of a radio signal generation method in a communication system. [Figure 7e] FIG. 10 is a conceptual diagram for explaining a third embodiment of a radio signal generation method in a communication system. [Figure 7f] FIG. 10 is a conceptual diagram for explaining a third embodiment of a radio signal generation method in a communication system. [Figure 7g] FIG. 10 is a conceptual diagram for explaining a third embodiment of a radio signal generation method in a communication system. [Figure 7h]FIG. 10 is a conceptual diagram for explaining a third embodiment of a radio signal generation method in a communication system. DETAILED DESCRIPTION OF THE INVENTION

[0029] Although the present disclosure can be modified in various ways and can have various embodiments, specific embodiments will be illustrated in the drawings and described in detail, but it should be understood that this is not intended to limit the disclosure to the specific embodiments, and that all modifications, equivalents, and alternatives within the spirit and technical scope of the present disclosure are included.

[0030] Terms such as "first," "second," etc. may be used to describe various components, but the components should not be limited by these terms. These terms are used only to distinguish one component from another. For example, a first component may be designated a "second component," and similarly, a second component may be designated a "first component," without departing from the scope of the present disclosure. The term "and / or" includes a combination of multiple related listed items or any of multiple related listed items.

[0031] When a component is said to be "coupled" or "connected" to another component, it should be understood that the component may be directly coupled or connected to the other component, but that there may be other components in between. Conversely, when a component is said to be "directly coupled" or "directly connected" to another component, it should be understood that there are no other components in between.

[0032] The terms used in this disclosure are merely used to describe specific embodiments and are not intended to limit the disclosure. A singular expression includes a plural expression unless the context clearly dictates otherwise. In this application, terms such as "comprise" or "have" are intended to specify the presence of features, numbers, steps, operations, components, parts, or combinations thereof described in the specification, and should be understood not to preclude the presence or possible addition of one or more other features, numbers, steps, operations, components, parts, or combinations thereof.

[0033] Unless otherwise defined, all terms used herein, including technical or scientific terms, have the same meaning as commonly understood by one of ordinary skill in the art to which this disclosure pertains. Terms as defined in commonly used dictionaries should be interpreted to have a meaning consistent with the meaning they have in the context of the relevant art, and should not be interpreted in an idealized or overly formal sense unless expressly defined in this disclosure.

[0034] A communication system to which an embodiment of the present disclosure is applied will be described. The communication system to which the embodiment of the present disclosure is applied is not limited to the content described below, and the embodiment of the present disclosure can be applied to various communication systems. Here, the term "communication system" may be used interchangeably with the term "communication network."

[0035] Throughout the specification, a network may include, for example, wireless internet such as WiFi (wireless fidelity), mobile internet such as WiBro (wireless broadband internet) or WiMax (world interoperability for microwave access), 2G mobile communication networks such as GSM (global system for mobile communication) or CDMA (code division multiple access), 3G mobile communication networks such as WCDMA (wideband code division multiple access) (registered trademark) or CDMA2000, 3.5G mobile communication networks such as HSDPA (high speed downlink packet access) or HSUPA (high speed uplink packet access), 4G mobile communication networks such as LTE (long term evolution) networks or LTE-Advanced networks, 5G mobile communication networks, B5G mobile communication networks (such as 6G mobile communication networks), etc.

[0036] Throughout the specification, the term "terminal" may refer to a mobile station, mobile terminal, subscriber station, portable subscriber station, user equipment, access terminal, etc., and may include all or some of the functionality of a terminal, mobile station, mobile terminal, subscriber station, portable subscriber station, user equipment, access terminal, etc.

[0037] Here, the terminals that can be used include a desktop computer, laptop computer, tablet PC, wireless phone, mobile phone, smartphone, smart watch, smart glass, e-book reader, portable multimedia player (PMP), portable game console, navigation device, digital camera, digital multimedia broadcasting (DMB) player, digital audio recorder, digital audio player, digital picture recorder, digital picture player, digital video recorder, digital video player, and the like, which are capable of communication.

[0038] Throughout this specification, a base station may refer to an access point, a radio access station, a node B, an evolved node B, a base transceiver station, a mobile multihop relay (MMR)-BS, etc., and may include all or some of the functions of a base station, access point, radio access station, a node B, an eNodeB, a base transceiver station, an MMR-BS, etc.

[0039] Hereinafter, preferred embodiments of the present disclosure will be described in more detail with reference to the accompanying drawings. In order to facilitate overall understanding of the present disclosure, the same reference numerals will be used for the same components in the drawings, and redundant descriptions of the same components will be omitted.

[0040] FIG. 1 is a conceptual diagram showing an embodiment of a communication system.

[0041] 1 , a communication system 100 may include multiple communication nodes 110-1, 110-2, 110-3, 120-1, 120-2, 130-1, 130-2, 130-3, 130-4, 130-5, and 130-6. The multiple communication nodes may support 4G communication (e.g., LTE (long term evolution) and LTE-A (advanced)) defined in 3GPP (3rd generation partnership project) standards, 5G communication (e.g., NR (new radio)), etc. 4G communication may be performed in a frequency band below 6 GHz, and 5G communication may be performed in a frequency band above 6 GHz as well as a frequency band below 6 GHz.

[0042] For example, for 4G and 5G communications, the plurality of communication nodes may support a code division multiple access (CDMA)-based communication protocol, a wideband CDMA (WCDMA)-based communication protocol, a time division multiple access (TDMA)-based communication protocol, a frequency division multiple access (FDMA)-based communication protocol, an orthogonal frequency division multiplexing (OFDM)-based communication protocol, a filtered OFDM-based communication protocol, a cyclic prefix (CP)-OFDM-based communication protocol, a discrete Fourier transform-spread-OFDM (DFT-s-OFDM)-based communication protocol, an orthogonal frequency division multiple access (OFDMA)-based communication protocol, a single carrier (SC)-FDMA-based communication protocol, a non-orthogonal multiple access (NOMA), a generalized frequency division multiplexing (GFDM)-based communication protocol, a filter bank multi-carrier (FBMC)-based communication protocol, a universal filtered multi-carrier (UFMC)-based communication protocol, a space division multiple access (SDMA)-based communication protocol, etc.

[0043] Furthermore, the communication system 100 may further include a core network. If the communication system 100 supports 4G communication, the core network may include a serving-gateway (S-GW), a packet data network (P-GW)-gateway (PDN (packet data network)-gateway), a mobility management entity (MME), etc. If the communication system 100 supports 5G communication, the core network may include a user plane function (UPF), a session management function (SMF), an access and mobility management function (AMF), etc.

[0044] Each of the plurality of communication nodes 110-1, 110-2, 110-3, 120-1, 120-2, 130-1, 130-2, 130-3, 130-4, 130-5, and 130-6 that make up the communication system 100 can have the following structure.

[0045] FIG. 2 is a block diagram showing an embodiment of a communication node that constitutes a communication system.

[0046] 2, the communication node 200 may include at least one processor 210, a memory 220, and a transceiver 230 that is coupled to a network for communication. The communication node 200 may further include an input interface unit 240, an output interface unit 250, a storage unit 260, etc. The components included in the communication node 200 are coupled to each other by a bus 270 to communicate with each other.

[0047] However, each component included in the communication node 200 may be connected via an individual interface or individual bus centered around the processor 210, rather than the common bus 270. For example, the processor 210 may be connected to at least one of the memory 220, the transceiver 230, the input interface unit 240, the output interface unit 250, and the storage unit 260 via a dedicated interface.

[0048] The processor 210 can execute program commands stored in at least one of the memory 220 and the storage device 260. The processor 210 refers to a central processing unit (CPU), a graphics processing unit (GPU), or a dedicated processor on which the methods according to the embodiments of the present disclosure are performed. The memory 220 and the storage device 260 may each be configured with at least one of a volatile storage medium and a non-volatile storage medium. For example, the memory 220 may be configured with at least one of a read-only memory (ROM) and a random access memory (RAM).

[0049] 1 , the communication system 100 may include multiple base stations 110-1, 110-2, 110-3, 120-1, and 120-2 and multiple terminals 130-1, 130-2, 130-3, 130-4, 130-5, and 130-6. The communication system 100 including the base stations 110-1, 110-2, 110-3, 120-1, and 120-2 and the terminals 130-1, 130-2, 130-3, 130-4, 130-5, and 130-6 may be referred to as an “access network.” The first base station 110-1, the second base station 110-2, and the third base station 110-3 may each form a macro cell. The fourth base station 120-1 and the fifth base station 120-2 may each form a small cell. The fourth base station 120-1, the third terminal 130-3, and the fourth terminal 130-4 may belong within the cell coverage of the first base station 110-1. The second terminal 130-2, the fourth terminal 130-4, and the fifth terminal 130-5 may belong within the cell coverage of the second base station 110-2. The fifth base station 120-2, the fourth terminal 130-4, the fifth terminal 130-5, and the sixth terminal 130-6 may belong within the cell coverage of the third base station 110-3. The first terminal 130-1 may belong within the cell coverage of the fourth base station 120-1. The sixth terminal 130-6 may belong within the cell coverage of the fifth base station 120-2.

[0050] Here, each of the multiple base stations 110-1, 110-2, 110-3, 120-1, and 120-2 can be referred to as a Node B, evolved Node B, base transceiver station (BTS), radio base station, radio transceiver, access point, access node, road side unit (RSU), radio remote head (RRH), transmission point (TP), transmission and reception point (TRP), eNB, gNB, etc.

[0051] Each of the multiple terminals 130-1, 130-2, 130-3, 130-4, 130-5, and 130-6 can be referred to as a UE (user equipment), terminal, access terminal, mobile terminal, station, subscriber station, mobile station, portable subscriber station, node, device, IoT (Internet of Things) device, on-board device (mounted module / device / terminal or on-board device / terminal, etc.), etc.

[0052] The base stations 110-1, 110-2, 110-3, 120-1, and 120-2 may operate in different frequency bands or the same frequency band. The base stations 110-1, 110-2, 110-3, 120-1, and 120-2 may be connected to each other via an ideal backhaul link or a non-ideal backhaul link, and may exchange information with each other via the ideal backhaul link or the non-ideal backhaul link. The base stations 110-1, 110-2, 110-3, 120-1, and 120-2 may be connected to the core network via the ideal backhaul link or the non-ideal backhaul link. Each of the multiple base stations 110-1, 110-2, 110-3, 120-1, and 120-2 can transmit signals received from the core network to the corresponding terminals 130-1, 130-2, 130-3, 130-4, 130-5, and 130-6, and can transmit signals received from the corresponding terminals 130-1, 130-2, 130-3, 130-4, 130-5, and 130-6 to the core network.

[0053] In addition, each of the multiple base stations 110-1, 110-2, 110-3, 120-1, and 120-2 can support MIMO transmission (e.g., single user (SU)-MIMO, multi user (MU)-MIMO, massive MIMO, etc.), coordinated multipoint (CoMP) transmission, carrier aggregation (CA) transmission, transmission in unlicensed bands, direct communication between terminals (device to device communication, D2D) (or proximity services (ProSe)), etc. Here, each of the plurality of terminals 130-1, 130-2, 130-3, 130-4, 130-5, and 130-6 may perform operations corresponding to the base stations 110-1, 110-2, 110-3, 120-1, and 120-2, and operations supported by the base stations 110-1, 110-2, 110-3, 120-1, and 120-2. For example, the second base station 110-2 may transmit a signal to the fourth terminal 130-4 based on the SU-MIMO scheme, and the fourth terminal 130-4 may receive a signal from the second base station 110-2 using the SU-MIMO scheme. Alternatively, the second base station 110-2 can transmit signals to the fourth terminal 130-4 and the fifth terminal 130-5 based on the MU-MIMO scheme, and each of the fourth terminal 130-4 and the fifth terminal 130-5 can receive signals from the second base station 110-2 using the MU-MIMO scheme.

[0054] Each of the first base station 110-1, the second base station 110-2, and the third base station 110-3 can transmit a signal to the fourth terminal 130-4 based on the CoMP scheme, and the fourth terminal 130-4 can receive signals from the first base station 110-1, the second base station 110-2, and the third base station 110-3 using the CoMP scheme. Each of the base stations 110-1, 110-2, 110-3, 120-1, and 120-2 can transmit and receive signals to and from terminals 130-1, 130-2, 130-3, 130-4, 130-5, and 130-6 within its cell coverage based on the CA scheme. The first base station 110-1, the second base station 110-2, and the third base station 110-3 can each control D2D between the fourth terminal 130-4 and the fifth terminal 130-5, and the fourth terminal 130-4 and the fifth terminal 130-5 can each perform D2D under the control of the second base station 110-2 and the third base station 110-3, respectively.

[0055] Next, a method for transmitting and receiving a wireless signal in a communication system will be described. Here, even when a method (e.g., signal transmission or reception) performed by a first communication node among communication nodes is described, a corresponding second communication node can perform a method (e.g., signal reception or transmission) equivalent to the method performed by the first communication node. For example, when an operation of a receiving node is described, a corresponding transmitting node can perform an operation equivalent to the operation of the receiving node. Conversely, when an operation of a transmitting node is described, a corresponding receiving node can perform an operation equivalent to the operation of the transmitting node.

[0056] FIG. 3 is a conceptual diagram illustrating an embodiment of a radio frame structure in a communication system.

[0057] Referring to FIG. 3, one radio frame in a communication system may be composed of 10 subframes, and one subframe may be composed of two time slots. One time slot may have multiple symbols in the time domain and may include multiple subcarriers in the frequency domain. The multiple symbols in the time domain may be OFDM symbols. Hereinafter, for convenience, an embodiment of a radio frame structure in a communication system will be described using an OFDM transmission mode as an example, in which the multiple symbols in the time domain are OFDM symbols. However, this is merely an example for convenience of explanation, and the embodiment of the radio frame structure in the communication system is not limited thereto. For example, other embodiments of the radio frame structure in a communication system may be configured to support other transmission modes, such as a single carrier (SC) transmission mode.

[0058] In one embodiment of the communication system, one or more of the numerologies in Table 1 can be used for various purposes, such as inter-carrier interference (ICI) reduction due to frequency band characteristics and latency reduction due to service characteristics. [Table 1]

[0059] Table 1 is merely an example for convenience of explanation, and the embodiment of the numerology used in the communication system is not limited thereto. Each numerology μ may correspond to information on a subcarrier spacing (SCS) Δf and a cyclic prefix (CP). The terminal can determine the numerology μ and CP value applied to the downlink bandwidth part or the uplink bandwidth part based on the higher layer parameters 'subcarrierSpacing', 'cyclicPrefix', etc.

[0060] The time resources for transmitting radio signals in the communication system 300 include one or more

number

number

number

number

[0061] In one embodiment of the communication system, a frame 330 may have a length of 10 ms, and a subframe 320 may have a length of 1 ms. Each frame 330 is divided into two half-frames having the same length, with the first half-frame (half-frame 0) consisting of subframes 320 numbered 0 through 4, and the second half-frame (half-frame 1) consisting of subframes 320 numbered 5 through 9. One carrier may have a set of frames for the uplink (uplink frames) and a set of frames for the downlink (downlink frames).

[0062] One slot can have six (in the case of an extended cyclic prefix) or seven (in the case of a normal cyclic prefix) OFDM symbols. The time-frequency region defined as one slot can be called a resource block (RB). If one slot has seven OFDM symbols, one subframe has 14 OFDM symbols.

number

[0063] A subframe may be divided into a control region and a data region. A physical downlink control channel (PDCCH) may be allocated to the control region. A physical downlink shared channel (PDSCH) may be allocated to the data region. Some of the subframes may be special subframes. The special subframes may include a downlink pilot time slot (DwPTS), a guard period (GP), and an uplink pilot time slot (UpPTS). The DwPTS can be used for time and frequency synchronization estimation and cell search of a terminal. The GP can be considered as a section for removing interference caused by multipath delay of a downlink signal.

[0064] In one embodiment of the communication system, a user can perform serving cell identification after acquiring time / frequency synchronization with the wireless network in order to connect to the network. Serving cell identification can be performed, for example, through physical cell identity (PCI) estimation using a predetermined synchronization signal. Each cell can have a different PCI and can transmit a synchronization signal including information for PCI identification (i.e., a synchronization signal indicating a PCI). For easy cell identification, the correlation characteristics between synchronization signals indicating different PCIs should be excellent, and the variability of the cross-correlation characteristics of all synchronization signal pairs should be as low as possible.

[0065] Furthermore, the number of distinguishable PCIs may be limited depending on the synchronization signal design method. To overcome this limitation and increase the number of distinguishable PCIs, one embodiment of a communication system may use a method of generating linearly distinct synchronization signals by cyclically shifting a cyclically distinct sequence. The sequence generated through this cyclic shift may not follow the correlation characteristics of the original sequence. This may result in degradation of the correlation characteristics between the generated synchronization signal pair, leading to a problem of high variability in the cross-correlation characteristics. A technology that can effectively increase the number of distinguishable PCIs while maintaining the correlation characteristics and variability of the synchronization signals may be required.

[0066] In one embodiment of the communication system, the synchronization signal may be configured based on one or more sequences. The one or more sequences constituting the synchronization signal may be arranged in a frame 330, a subframe 320, a slot 310, or an OFDM symbol constituting a slot 310 in the time domain. The one or more sequences constituting the synchronization signal may be modulated and mapped to multiple subcarriers in the frequency domain. In one embodiment of the communication system, the one or more sequences constituting the synchronization signal may correspond to one or more binary sequences or complex sequences.

[0067] FIG. 4 is a flowchart illustrating a first embodiment of a signal transmission and reception method in a communication system.

[0068] Referring to Fig. 4, a communication system 400 may include multiple communication nodes. For example, the communication system 400 may include at least a first communication node 401 and a second communication node 402. The first communication node 401 may be the same as or similar to the cell that transmits a synchronization signal, as described with reference to Fig. 3. The second communication node 402 may be the same as or similar to the receiving node that receives a synchronization signal, as described with reference to Fig. 3. Hereinafter, in describing an embodiment of a signal transmission and reception method in a communication system with reference to Fig. 4, content that overlaps with that described with reference to Figs. 1 to 3 may be omitted.

[0069] In one embodiment of the communication system 400, the first communication node 401 may correspond to a cell, a base station, a network, etc. The first communication node 401 may transmit a first signal including identification information used by a user (UE, terminal, etc.) within the coverage of the first communication node 401 to identify the first communication node 401. For example, the first communication node 401 may be identified by the first identification information. The first identification information may correspond to a physical cell identity (PCI). Alternatively, the first identification information may correspond to information on the PCI. The first identification information may be generated based on the PCI. The first signal including the first identification information may correspond to a synchronization signal. The first signal may correspond to a secondary synchronization signal (SSS). However, this is merely an example for convenience of explanation, and the first embodiment of the signal transmission and reception method in the communication system 400 is not limited thereto. The first signal may be composed of one or more sequences (hereinafter, one or more first signal sequences). The second communication node 402 can receive the first signal transmitted from the first communication node 401. The second communication node 402 can identify the first communication node 401 based on the received first signal.

[0070] Specifically, the first communication node 401 may generate one or more binary sequences (S410). The one or more binary sequences may correspond to PN sequences. The PN sequences may be referred to as "m-sequences." The first communication node 401 may generate one or more first signal sequences based on the one or more binary sequences (S420).

[0071] The first communication node 401 may modulate the one or more first signal sequences generated in step S420 and allocate (or map) them to radio resources (S430). For example, the first communication node 401 may modulate the one or more first signal sequences generated to generate one or more modulation symbols. The first communication node 401 may allocate the one or more generated modulation symbols to time resources and / or frequency resources.

[0072] The first communication node 401 can transmit a first signal consisting of one or more first signal sequences modulated and mapped to radio resources to the second communication node 402 (S440). In other words, the first communication node 401 can transmit a first signal consisting of one or more modulation symbols modulated with one or more first signal sequences to the second communication node 402.

[0073] The second communication node 402 may receive a first signal transmitted from the first communication node 401 (S440). The second communication node may perform an identification operation for the first communication node 401 based on the first signal received in step S440 (S450). The identification in step S450 may include, for example, cell identification.

[0074] 5a and 5b are conceptual diagrams for explaining a first embodiment of a radio signal structure in a communication system.

[0075] 5a and 5b, a communication system may include a plurality of communication nodes. The communication system may be the same as or similar to the communication system 400 described with reference to Fig. 4. Hereinafter, in describing a first embodiment of a radio signal structure in the communication system with reference to Figs. 5a and 5b, content that overlaps with that described with reference to Figs. 1 to 4 may be omitted.

[0076] The first communication node can generate and transmit a wireless signal to a second communication node. The first communication node can generate one or more wireless signals. The first communication node can generate one or more wireless signal sequences to generate the one or more wireless signals. The first communication node can modulate one or more elements constituting the generated one or more wireless signal sequences and map them to one or more subcarriers in the frequency domain.

[0077] In one embodiment of the communication system, when the number of one or more subcarriers to which one or more radio signal sequences are mapped is a natural number N equal to or greater than 1, a subcarrier index k may have a value of a natural number equal to or greater than 0 and equal to or less than N-1. That is, k may be 0, 1, ..., N-1. The one or more radio signal sequences may be generated based on a predetermined identification index v. Here, the identification index v may correspond to, for example, the first identification information described with reference to FIG. 4. The identification index v may correspond to the first identification information. The identification index v may be determined based on the first identification information. Alternatively, the first identification information may be determined based on the identification index v. The one or more radio signal sequences may be, for example, S v (k). Alternatively, one or more radio signal sequences may be distinguished by their generation schemes, and S v、1 (k), S v、2 (k), S v、3 (k), S v、4 It can also be expressed as (k).

[0078] In one embodiment of the communication system, the first wireless signal may correspond to the first signal described with reference to Fig. 4. The first wireless signal may correspond to a synchronization signal, SSS, etc. Alternatively, the first wireless signal may correspond to a newly defined signal for cell identification. The first signal may also be referred to as an "identification signal."

[0079] In one embodiment of the communication system, a radio signal sequence S v (k) can be generated based on two binary sequences. v (k) is a set of N elements (S v (0), S v (1), ..., S v (N-1)) can be composed of the radio signal sequence S v (k) can be modulated and mapped to N subcarriers. Figures 5a and 5b show the case where N is greater than 1 (i.e., the wireless signal sequence S v It can be seen that (k) is modulated and mapped to a plurality of subcarriers. However, this is merely an example for convenience of explanation, and the first embodiment of the wireless signal structure in the communication system is not limited thereto.

[0080] Referring to FIG. 5a, in a first wireless signal structure 500, a wireless signal sequence S v (k) can be modulated and mapped onto N subcarriers represented by index k (k=0, 1, ..., N-1). v (k) consists of N elements (S v (0), S v (1), ..., S v (N-1)) can be mapped to a subcarrier having a corresponding index. v (k) are mapped to N subcarriers (i.e., the radio signal sequence S v(N subcarriers onto which k-modulated modulation symbols are mapped) may be included in a first subcarrier group. The N subcarriers constituting the first subcarrier group may be adjacent to or spaced apart from one another in the frequency domain. While FIG. 5a illustrates a case in which at least some of the N subcarriers constituting the first subcarrier group are arranged adjacent to one another, this is merely an example for convenience of explanation, and the first embodiment of the radio signal structure in the communication system is not limited thereto. For example, the first subcarrier group may be composed of N subcarriers that are spaced apart from one another. In other words, the first subcarrier group may be composed of N subcarriers that are not adjacent to one another.

[0081] One or more null subcarriers may be arranged around or between the N subcarriers constituting the first subcarrier group. Null subcarriers may not carry signals. In other words, no modulation symbols may be assigned to null subcarriers. Null subcarriers may have a value of 0. Null subcarriers may also correspond to gap subcarriers, direct current (DC) subcarriers, etc. Null subcarriers may be arranged to easily identify each subcarrier.

[0082] A null subcarrier may be arranged at the front and / or rear end of the first subcarrier group in the frequency domain. For example, a null subcarrier may be arranged at the front end of a subcarrier corresponding to subcarrier index 0 and / or the rear end of a subcarrier corresponding to subcarrier index N-1. One or more null subcarriers may also be arranged among the N subcarriers constituting the first subcarrier group. For example, a null subcarrier may be arranged at the front and / or rear end of one or more central subcarriers (hereinafter referred to as central subcarriers) among the N subcarriers constituting the first subcarrier group. Alternatively, the first subcarrier group may be divided into a plurality of subgroups, each including one or more subcarriers. A null subcarrier may be arranged at the front and / or rear end of each subgroup.

[0083] Referring to FIG. 5b, in a second radio signal structure 550, a radio signal sequence S v (k) can be modulated and mapped onto N subcarriers, represented by index k (k=0, 1, ..., N-1). Here, the wireless signal sequence S v The N subcarriers to which (k) is mapped may be included in a second subcarrier group. The second subcarrier group may be composed of N subcarriers at least some of which are adjacent to each other in the frequency domain. Here, there may be no null subcarriers between the N subcarriers constituting the second subcarrier group.

[0084] 6a to 6d are conceptual diagrams for explaining first and second embodiments of a radio signal generation method in a communication system.

[0085] 6a and 6b, a communication system may include multiple communication nodes. The communication system may be the same as or similar to the communication system 400 described with reference to FIG. 4. In the communication system, a wireless signal may have the same or similar structure as the first wireless signal structure 500 described with reference to FIG. 5a or the second wireless signal structure 550 described with reference to FIG. 5b. Hereinafter, when describing the first and second embodiments of the wireless signal generation method with reference to FIGS. 6a and 6b, content that overlaps with that described with reference to FIGS. 1 to 5b may be omitted.

[0086] FIG. 6a is a conceptual diagram for explaining a first embodiment of a radio signal generation method in a communication system.

[0087] <First embodiment of wireless signal generation method> In one embodiment of the communication system, the first communication node may generate a radio signal according to a first embodiment of a radio signal generation scheme. The first embodiment of the radio signal generation scheme may be referred to as a "Binary Phase Shift Keying (BPSK) scheme." The first embodiment of the radio signal generation scheme may be referred to as a "Random BPSK scheme."

[0088] In the first embodiment of the radio signal generation scheme, the first radio signal may be generated based on one or more basic radio signal sequences. The one or more basic radio signal sequences may be generated based on one or more binary sequences. In other words, the one or more basic radio signal sequences may correspond to results of one or more binary sequences being converted according to the first embodiment of the radio signal generation scheme. For example, the one or more binary sequences may correspond to a pseudo-noise (PN) sequence or a binary PN sequence. The one or more binary sequences may also correspond to an m-sequence. Alternatively, the one or more binary sequences may be a Gold sequence generated by element-wise exclusive-OR (XOR) operation on two different PN sequences.

[0089] In one embodiment of the communication system, a basic radio signal sequence S v (k) may be generated based on two first binary sequences x0(i) and x1(i). For example, the basic radio signal sequence S v (k) may be defined the same as or similar to Equation 1.

number

[0090] In Formula 1, [a] b means the b-modulo operation on the a value.

number

[0091] In Equation 1, Ξ means the number of distinguishable values ​​of the identification index v. That is, the number of values ​​that the identification index v can have may correspond to Ξ=1008. The basic wireless signal sequence S generated by Equation 1 v Depending on (k), a total of 1008 identification indexes can be identified. However, this is merely an example for the convenience of explanation, and the first embodiment of the wireless signal generation method is not limited to this.

[0092] Theoretically, the basic radio signal sequence S v The maximum number of distinguishable identification indices based on (k) is the number of the basic radio signal sequence S vThe basic radio signal sequence S(k) can be defined by all possible combinations of cyclic shift indexes of the two first binary sequences x0(i) and x1(i). Each of the cyclic shift indexes v0 and v1 associated with the two first binary sequences x0(i) and x1(i) can have a total of 127 values. Therefore, theoretically, the basic radio signal sequence S v The maximum number of distinguishable indexes based on (k) is 127. 2 = 16129. v (k) can have up to 127 cyclically distinct sequences.

[0093] In one embodiment of the communication system, the value of the identification index v may be selected between 0 and Ξ-1. If v=19 is selected, it may be calculated as g=6, g0=0, g1=6, and u=1 based on Equation 1. In this case, the cyclic shift indexes associated with the two first binary sequences x0(i) and x1(i) may be calculated as v0=5 and v1=6. Based on the values ​​of the cyclic shift indexes v0 and v1 thus calculated, the basic radio signal sequence S v (k) can be calculated.

[0094] In Equation 1, a basic radio signal sequence S is generated based on two first binary sequences x0(i) and x1(i). v The formula for calculating (k) is "S v (k)=(1-2(x0([k+v0] 127 ))(1-2(x1([k+v1] 127 ))" can correspond to BPSK operations. The basic radio signal sequence S v (k) can have the value of real number 1 or -1.

[0095] FIG. 6a shows a basic radio signal sequence S generated based on Equation 1 in the first embodiment of the radio signal generation method. v (k), or the basic radio signal sequence S v6 shows an embodiment of a constellation map (hereinafter, referred to as a basic constellation map) 610 for a first wireless signal generated based on (k). The first wireless signal may be represented by two constellation points on the basic constellation map 610. Both of the two constellation points corresponding to the first wireless signal may have a real value of 1 or −1.

[0096] 6b to 6d are conceptual diagrams for explaining a second embodiment of a radio signal generation method in a communication system.

[0097] <Second embodiment of wireless signal generation method> In one embodiment of the communication system, the first communication node may generate a radio signal according to a second embodiment of the radio signal generation method. The second embodiment of the radio signal generation method may be referred to as a "Quadrature Phase Shift Keying (QPSK) method." The second embodiment of the radio signal generation method may be referred to as a "Random QPSK method." The second embodiment of the radio signal generation method may be referred to as a "π / 4 QPSK method."

[0098] In a second embodiment of the radio signal generation method, the first radio signal may be generated based on one or more first radio signal sequences. The one or more first radio signal sequences may be generated based on one or more binary sequences. The one or more first radio signal sequences may be generated based on S v、1 It can be expressed as (k).

[0099] In one embodiment of the communication system, a first radio signal sequence S v、1 The first radio signal sequence S(k) may be generated based on the second binary sequence x2(i) and the third binary sequence x3(i). v、1 (k) is the first intermediate sequence Ψ v (m), and a first intermediate sequence Ψ v(m) may be defined based on the second binary sequence x2(i) and the third binary sequence x3(i). The second binary sequence x2(i) and the third binary sequence x3(i) may correspond to PN sequences. For example, the first wireless signal sequence S v、1 (k) may be defined the same as or similar to Equation 2.

number

[0100] In Equation 2, the value of N may be 127. The second binary sequence x2(i) and the third binary sequence x3(i) may be defined based on different generator polynomials having a maximum degree of 8. The second binary sequence x2(i) may be determined based on a second recurrence formula: x2(i+8) = [x2(i+7) + x2(i+6) + x2(i+5) + x2(i+2) + x2(i+1) + x2(i)]2. The third binary sequence x3(i) may be determined based on a third recurrence formula: x3(i+8) = [x3(i+7) + x3(i+6) + x3(i+1) + x3(i)]2. The recurrence formulas and numbers shown in Equation 2 are merely examples for convenience of explanation, and the second embodiment of the wireless signal generation method is not limited thereto. For example, the second binary sequence x2(i) and the third binary sequence x3(i) can be generated in various ways other than the recurrence formula shown in Equation 2.

[0101] Theoretically, the first radio signal sequence S v、1 The maximum number of distinguishable identification indices based on (k) is the first radio signal sequence S v、1 The first radio signal sequence S(k) can be defined as a combination of all possible cyclic shift indexes of the second binary sequence x2(i) and the third binary sequence x3(i). The cyclic shift indexes v2 and v3 associated with the second binary sequence x2(i) and the third binary sequence x3(i) can have a total of 255 values. Therefore, theoretically, the first radio signal sequence S v、1The maximum number of distinguishable identification indexes based on (k) can be 2552=65025. v、1 (k) can have up to 255 cyclically distinct sequences.

[0102] In Equation 2, Ξ denotes the number of distinguishable identification index v values. The first wireless signal sequence S generated by Equation 2 v、1 Depending on (k), a total of Ξ identification indexes can be identified. In one embodiment of the communication system, the value of the identification index v can be selected between 0 and Ξ-1. If v is selected as 999, then g=333 based on Equation 2,

number

[0333] Ω , u=0. In this case, the circular shift index associated with the two first binary sequences x0(i) and x1(i) can be calculated as

number

[0333] Ω Based on the values ​​of the cyclic shift indexes v2 and v3 calculated in this way, the first radio signal sequence S v、1 (k) can be calculated, where Ω can be calculated based on Ξ. For example, Ω can be calculated based on Ξ in the same or similar manner as in Equation 3.

number

[0103] In Equation 3,

number

[0104] In Equation 2, a first intermediate sequence Ψ is calculated based on the second binary sequence x2(i) and the third binary sequence x3(i). v The formula to calculate (m) is "Ψ v (m)=1-2[x2([m+v2] 255 ))+x3([m+v3] 255 )2” can correspond to a BPSK operation. v (m) can have the value of real number 1 or -1.

[0105] On one side of FIG. 6b, a first intermediate sequence Ψ generated based on Equation 2 in the second embodiment of the wireless signal generation method is shown. v It can be seen that one embodiment of a constellation map for (m) (hereinafter referred to as the first intermediate constellation map) 620 is shown. The first intermediate constellation map 620 may be the same as or similar to the base constellation map 610 described with reference to FIG. 6a.

[0106] In Equation 2, the first intermediate sequence Ψ calculated based on BPSK arithmetic v (m) based on the first radio signal sequence S v、1 Formula to calculate (k)

number

number

number

number

[0107] On the other hand, in FIG. 6b, a first radio signal sequence S generated based on Equation 2 in the second embodiment of the radio signal generation method is shown. v、1 (k), or the first radio signal sequence S v、16 shows an embodiment of a constellation map (hereinafter, first final constellation map) 630 for a first wireless signal generated based on (k). The first wireless signal may be represented by four constellation points on the first final constellation map 630. Each of the four constellation points corresponding to the first wireless signal may have complex coordinates having a real part and an imaginary part on the complex plane.

[0108] The second final constellation map 640 shown in FIG. 6c shows the first radio signal sequence S corresponding to each of the four constellation points displayed on the first final constellation map 630. v、1 (k) and the first intermediate sequence Ψ v In the second final constellation map 640, the constellation point "00" corresponds to the value of Ψ v (2k)=1, and Ψ v This corresponds to the case where (2k+1)=1. The constellation point "01" corresponds to the case where Ψ v (2k)=1, and Ψ v This corresponds to the case where (2k+1)=-1. The constellation point "10" is v (2k)=-1, and Ψ v This corresponds to the case where (2k+1)=1. The constellation point "11" corresponds to the case where Ψ v (2k)=-1, and Ψ v On the second final constellation map 640, the first radio signal sequence S corresponding to the constellation point 00 can be handled as follows: v、1 The value of (k) is

number

number

number

number

[0109] In addition, in Equation 2, the first intermediate sequence Ψ v (m) based on the first radio signal sequence S v、1 The formula for calculating (k) is:

number

number

[0110] FIG. 6d shows the first radio signal sequence S generated based on the modified Equation 4. v、1 (k), or the first radio signal sequence S v、1 It can be seen that an embodiment of a constellation map for the first wireless signal generated based on (k) (hereinafter referred to as the third final constellation map) 650 is shown. In the third final constellation map 650, the first wireless signal sequence S corresponding to the constellation point 00 is v、1 The value of (k) is

number

number

number

number

[0111] The basic radio signal sequence S generated based on Equation 1 v (k) and the first radio signal sequence S generated based on Equation 2 or Equation 4 v、1 (k) can be compared identically or similarly to Table 4. [Table 4]

[0112] Referring to Table 4, the basic radio signal sequence S v (k) and the first radio signal sequence S v、1 The number N of subcarriers onto which (k) is mapped after modulation may be equal to 127. However, the maximum number of cyclically distinct sequences, 16129 and 65025, may differ by a factor of about four. That is, the first radio signal sequence S v、1 The first radio signal generated based on (k) is a basic radio signal sequence S v (k) can support four times more identification indexes while using the same amount of frequency resources as the first radio signal generated based on (k). v、1 (k) is generated based on a cyclically distinguishable sequence, so that the first radio signal sequence S v、1(k) can maintain the correlation characteristics and variability between the synchronization signal pairs generated based on the first wireless signal sequence S v、1 (k) is the basic radio signal sequence S v While having the advantages shown in Table 4 compared to (k), the first radio signal sequence S has excellent correlation characteristics and less fluctuation in correlation characteristics. v、1 The first radio signal generated based on (k) can have an advantage of being robust against an integer multiple of a carrier frequency offset (CFO).

[0113] 7a to 7h are conceptual diagrams for explaining a third embodiment of a radio signal generation method in a communication system.

[0114] 7a to 7h, a communication system may include a plurality of communication nodes. The communication system may be the same as or similar to the communication system 400 described with reference to FIG. 4. In the communication system, a second wireless signal may have the same or similar structure as the first wireless signal structure 500 described with reference to FIG. 5a or the second wireless signal structure 550 described with reference to FIG. 5b. Hereinafter, in describing the third embodiment of the wireless signal generation method with reference to FIGS. 7a to 7b, content that overlaps with that described with reference to FIGS. 1 to 6b may be omitted.

[0115] <Third embodiment of wireless signal generation method> In one embodiment of the communication system, the first communication node can generate a second radio signal according to a third embodiment of the radio signal generation method. In the third embodiment of the radio signal generation method, the second radio signal can be generated based on one or more second radio signal sequences. The one or more second radio signal sequences can be generated based on one or more binary sequences. The one or more second radio signal sequences can be generated based on S v、2 It can be expressed as (k).

[0116] In one embodiment of the communication system, the second radio signal sequence Sv、2 The second radio signal sequence S(k) may be generated based on the second binary sequence x2(i) and the third binary sequence x3(i). v、2 (k) is the first intermediate sequence Ψ v (m), and a first intermediate sequence Ψ v (m) may be defined based on the second binary sequence x2(i) and the third binary sequence x3(i). The second binary sequence x2(i) and the third binary sequence x3(i) may correspond to PN sequences. For example, the second wireless signal sequence S v、2 (k) may be defined the same as or similar to Equation 5.

number

[0117] Equation 5 may be partially the same as Equation 2 described with reference to the second embodiment of the wireless signal generation method, but may also be partially different. v (m) based on the second radio signal sequence S v、2 Formula to calculate (k)

number

number

number

number

[0118] 7a and 7b show the second radio signal sequence S generated based on Equation 5 in the third embodiment of the radio signal generation method. v、2 (k), or the second radio signal sequence S v、2 It can be seen that embodiments of constellation maps for a second radio signal generated based on (k) (hereinafter, first constellation map 710 and second constellation map 720) are shown.

[0119] The first constellation map 710 is

number

[0120] A second radio signal sequence S, represented by four constellation points on the first constellation map 710 shown in FIG. 7a, v、2(k) is the first radio signal sequence S defined as in Equation 2. v、1 6d, the four constellation points on the first constellation map 710 may correspond to the result of performing a rotational transformation operation of size π / 4 on the complex plane on (k). In other words, the four constellation points on the first constellation map 710 may correspond to the result of shifting the four constellation points on the second final constellation map 640 shown in FIG. 6d by a rotation angle of π / 4 on the complex plane.

[0121] The second constellation map 720 is

number

[0122] A second radio signal sequence S, represented by four constellation points, for example, on a second constellation map 720 shown in FIG. 7b. v、2 (k) is the first radio signal sequence S defined as in Equation 2. v、16d, the four constellation points on the second final constellation map 640 may correspond to the result of performing a rotational transformation operation of −π / 4 size on the complex plane on (k). In other words, the four constellation points on the second final constellation map 720 may correspond to the result of shifting the four constellation points on the second final constellation map 640 shown in FIG. 6d by a rotation angle of −π / 4 on the complex plane.

[0123] The second radio signal sequence S described with reference to Figs. 7a and 7b v、2 (k) is merely an example for convenience of explanation, and the second embodiment of the wireless signal generation method is not limited thereto. For example, in one embodiment of the communication system, the second wireless signal sequence S v、2 The definition of (k) can be changed as shown in Equation 6.

number

[0124] In Equation 6, the first intermediate sequence Ψ v (m) based on the second radio signal sequence S v、2 Formula to calculate (k)

number

number

number

number

number

number

[0125] In Fig. 7c, the second radio signal sequence S v、2 (k) or a third embodiment of a constellation map for the second radio signal (hereinafter referred to as the third constellation map) 730 is shown. On the third constellation map 730, the second radio signal sequence S corresponding to the constellation point 00 is v、2 The value of (k) may be an imaginary number j. The second radio signal sequence S corresponding to the constellation point O1 v、2 The value of (k) can be a real number −1. The second radio signal sequence S corresponding to the constellation point 10 v、2 The value of (k) can be the real number 1. The second radio signal sequence S corresponding to the constellation point 11 v、2 The value of (k) can be an imaginary number -j.

[0126] The second radio signal sequence S is represented by, for example, four constellation points on the third constellation map 730 shown in FIG. 7c. v、2 (k) is the basic radio signal sequence S defined as in Equation 4. v、16d, the four constellation points on the third final constellation map 650 may be shifted by a rotation angle of 3π / 4 on the complex plane.

[0127] In Fig. 7d, the second radio signal sequence S v、2 (k) or a fourth embodiment of a constellation map for the second radio signal (hereinafter referred to as the fourth constellation map) 740 is shown. On the fourth constellation map 740, the second radio signal sequence S corresponding to the constellation point 00 is v、2 The value of (k) may be the real number 1. The second radio signal sequence S corresponding to the constellation point O1 v、2 The value of (k) may be an imaginary number j. v、2 The value of (k) may be an imaginary number -j. v、2 The value of (k) can be a real number -1.

[0128] The second radio signal sequence S is represented by four constellation points, such as four constellation points, on the fourth constellation map 740 shown in FIG. 7d. v、2 (k) is the basic radio signal sequence S defined as Equation 2. v、1 6d, the four constellation points on the fourth constellation map 740 may correspond to the result of performing a rotational transformation operation of size 3π / 4 on the complex plane on (k). In other words, the four constellation points on the fourth constellation map 740 may correspond to the result of shifting the four constellation points on the second final constellation map 640 shown in FIG. 6d by a rotation angle of 3π / 4 on the complex plane.

[0129] In Fig. 7e, the second radio signal sequence S v、2(k) or a fifth embodiment of a constellation map for the second radio signal (hereinafter, referred to as the fifth constellation map) 750 is shown. On the fifth constellation map 750, the second radio signal sequence S corresponding to the constellation point 00 is v、2 The value of (k) may be the real number 1. The second radio signal sequence S corresponding to the constellation point O1 v、2 The value of (k) may be an imaginary number j. v、2 The value of (k) may be an imaginary number -j. v、2 The value of (k) can be a real number -1.

[0130] The second radio signal sequence S is represented by four constellation points, such as four constellation points, on the fifth constellation map 750 shown in FIG. 7e. v、2 (k) is the basic radio signal sequence S defined as in Equation 4. v、1 6d, the four constellation points on the fifth constellation map 750 may correspond to the result of performing a rotational transformation operation of −π / 4 size on the complex plane on (k). In other words, the four constellation points on the fifth constellation map 750 may correspond to the result of shifting the four constellation points on the third final constellation map 650 shown in FIG. 6d by a rotation angle of −π / 4 on the complex plane.

[0131] In Fig. 7f, the second radio signal sequence S v、2 (k) or a sixth embodiment of a constellation map for the second radio signal (hereinafter, referred to as the sixth constellation map) 760 is shown. On the sixth constellation map 760, the second radio signal sequence S corresponding to the constellation point 00 is v、2 The value of (k) can be a real number −1. The second radio signal sequence S corresponding to the constellation point O1 v、2 The value of (k) may be an imaginary number -j. v、2The value of (k) may be an imaginary number j. v、2 The value of (k) can be a real number 1.

[0132] The second radio signal sequence S is displayed as four constellation points on the sixth constellation map 760 shown in FIG. v、2 (k) is the basic radio signal sequence S defined as in Equation 4. v、1 6d, the four constellation points on the sixth constellation map 760 may correspond to the result of performing a rotational transformation operation of −3π / 4 size on the complex plane on (k). In other words, the four constellation points on the sixth constellation map 760 may correspond to the result of shifting the four constellation points on the third final constellation map 650 shown in FIG. 6d by a rotation angle of −3π / 4 on the complex plane.

[0133] In Figure 7g, the second radio signal sequence S v、2 (k) or a seventh embodiment of a constellation map for the second radio signal (hereinafter, the seventh constellation map) 770 is shown. On the seventh constellation map 770, the second radio signal sequence S corresponding to the constellation point 00 is v、2 The value of (k) may be an imaginary number -j. The second radio signal sequence S corresponding to the constellation point O1 v、2 The value of (k) may be the real number 1. The second radio signal sequence S corresponding to the constellation point 10 v、2 The value of (k) can be a real number −1. The second radio signal sequence S corresponding to the constellation point 11 v、2 The value of (k) can be an imaginary number j.

[0134] The second radio signal sequence S is represented by, for example, four constellation points on the seventh constellation map 770 shown in FIG. 7g. v、2 (k) is the basic radio signal sequence S defined as in Equation 4. v、16d, the four constellation points on the seventh constellation map 770 may correspond to the result of performing a rotational transformation operation of −π / 4 size on the complex plane on (k). In other words, the four constellation points on the seventh constellation map 770 may correspond to the result of shifting the four constellation points on the third final constellation map 650 shown in FIG. 6d by a rotation angle of −π / 4 on the complex plane.

[0135] In Figure 7h, the second radio signal sequence S v、2 (k) or an eighth embodiment of a constellation map for the second radio signal (hereinafter, referred to as the eighth constellation map) 780 is shown. On the eighth constellation map 780, the second radio signal sequence S corresponding to the constellation point 00 is v、2 The value of (k) may be an imaginary number -j. The second radio signal sequence S corresponding to the constellation point O1 v、2 The value of (k) can be a real number −1. The second radio signal sequence S corresponding to the constellation point 10 v、2 The value of (k) can be the real number 1. The second radio signal sequence S corresponding to the constellation point 11 v、2 The value of (k) can be an imaginary number j.

[0136] The second radio signal sequence S is displayed as four constellation points on the eighth constellation map 780 shown in FIG. 7h. v、2 (k) is the basic radio signal sequence S defined as Equation 2. v、1 6d, the four constellation points on the eighth constellation map 780 may correspond to the result of performing a rotational transformation operation of −3π / 4 size on the complex plane on (k). In other words, the four constellation points on the eighth constellation map 780 may correspond to the result of shifting the four constellation points on the second final constellation map 640 shown in FIG. 6d by a rotation angle of −3π / 4 on the complex plane.

[0137] In the first to eighth constellation maps 710, ..., 780 described with reference to Figures 7a to 7h, the four constellation points corresponding to the second radio signal generated by the third embodiment of the radio signal generation method may all be located on the real axis or the imaginary axis in the complex plane. The third embodiment of the radio signal generation method may be referred to as an "Axis QPSK (AQPSK) method" or an "AQPSK generation method."

[0138] The second communication node receives the second radio signal sequence S generated by the third embodiment of the radio signal generation method. v、2 The second communication node can generate a second wireless signal based on (k). The second communication node can transmit the second wireless signal generated based on the third embodiment of the wireless signal generation method to the second communication node. The second communication node can receive the second wireless signal. The second communication node can perform an estimation operation, an identification operation, or the like based on the second wireless signal. Here, the second wireless signal sequence S generated by the third embodiment of the wireless signal generation method v、2 (k) may have a real value (e.g., 1, -1) or a pure imaginary value (e.g., j, -j). As a result, when the second communication node performs an estimation operation or an identification operation based on the second radio signal generated according to the third embodiment of the radio signal generation method, a separate complex multiplication operation may not be required. Such an estimation operation or identification operation may require a smaller amount of calculation (or amount of calculation resources) and may have lower computational complexity than the estimation operation or identification operation based on the first radio signal generated according to the second embodiment of the radio signal generation method described with reference to FIGS. 6b to 6d. That is, the performance of the estimation operation or identification operation performed by the communication node receiving the second radio signal generated according to the third embodiment of the radio signal generation method may be improved.

[0139] In addition, the second wireless signal generated by the third embodiment of the wireless signal generation method may have the same or similar advantages as the first wireless signal generated by the second embodiment of the wireless signal generation method.

[0140] <Fourth embodiment of wireless signal generation method> In one embodiment of the communication system, the first communication node can generate a third radio signal according to a fourth embodiment of the radio signal generation method. In the fourth embodiment of the radio signal generation method, the third radio signal can be generated based on one or more third radio signal sequences. The one or more first radio signal sequences can be generated based on one or more binary sequences. The one or more third radio signal sequences can be generated based on S v、3 It can be expressed as (k).

[0141] In one embodiment of the communication system, the third radio signal sequence S v、3 (k) may be generated based on the fourth binary sequence x4(i), the fifth binary sequence x5(i), and the sixth binary sequence x6(i). The fourth binary sequence x4(i), the fifth binary sequence x5(i), and the sixth binary sequence x6(i) may correspond to PN sequences. For example, the third wireless signal sequence S v、3 (k) may be defined the same as or similar to Equation 7.

number

[0142] In Equation 7, the value of N can be 126 or 127. When N is 126, it can be considered that one of the 127 subcarriers (e.g., the center subcarrier) in the first subcarrier group described with reference to FIG. 5a is excluded from the indexing. When N is 127, it can be considered that the center subcarrier among the 127 subcarriers in the first subcarrier group is included in the indexing, and the value assigned to the center subcarrier is 0. The third wireless signal sequence S defined based on Equation 7 can be considered as follows: v、3 The elements constituting (k) may be divided into a first element group and a second element group based on the center subcarrier.

[0143] The fourth binary sequence x4(i) and the fifth binary sequence x5(i) may be defined based on different generator polynomials having a maximum degree of 6. The fourth binary sequence x4(i) may be determined based on the fourth recurrence formula "x4(i+6) = [x4(i+1) + x4(i+0)]2." The fifth binary sequence x5(i) may be determined based on the fifth recurrence formula "x5(i+6) = [x5(i+5) + x5(i+2) + x5(i+1) + x5(i+0)]2." The sixth binary sequence x6(i) may be defined based on a generator polynomial having a maximum degree of 3. The sixth binary sequence x6(i) may be determined based on the sixth recurrence formula "x6(i+3) = [x6(i+2) + x6(i+0)]2." The recurrence formula and numbers shown in Equation 7 are merely examples for convenience of explanation, and the fourth embodiment of the wireless signal generation method is not limited thereto. For example, the fourth binary sequence x4(i), the fifth binary sequence x5(i), and the sixth binary sequence x6(i) can be generated in various ways other than the recurrence formula shown in Equation 7.

[0144] In one embodiment of the communication system, the third radio signal sequence S v、3 The N elements constituting (k) may be divided into a first group and a second group. For example, the third radio signal sequence S v、3 (k) may be generated based on a first group (or first element group) consisting of N / 2 elements and a second group (or second element group) consisting of N / 2 elements.

[0145] In one embodiment of the communication system, the first group is S v、3 [k], and the second group is S v、3 It can be expressed as [k+N / 2]. First group S v、3 [k] and the second group S v、3 In [k+N / 2], k can have a value greater than or equal to 0 and less than N / 2. In Equation 7, the third wireless signal sequence S is calculated based on the fourth binary sequence x4(i), the fifth binary sequence x5(i), and the sixth binary sequence x6(i).v、3 (k) First Group S v、3 The formula for calculating [k] is "S v、3 [k]=1-2[x4([k+v4] 63 )+x5([k+v5] 63 )+x6([k+v6]7)]2" can correspond to BPSK operation. Note that the third radio signal sequence S v、3 (k) Second Group S v、3 [k+N / 2] is the first group S v、3 [k] repetitions, whereby a third radio signal sequence S including the first and second groups is generated. v、3 (k) can have a real value of 1 or −1. Alternatively, in one embodiment of the communication system, the first group is an intermediate sequence S v、3 In this case, the second group can be determined based on the intermediate sequence S v、3 Iteration [k] (i.e., S v、3 [k+N / 2]).

[0146] Theoretically, the third radio signal sequence S v、3 The maximum number of distinguishable identification indexes based on (k) is the third radio signal sequence S v、3 The third wireless signal sequence S(k) can be defined as a combination of all possible cyclic shift indexes of the fourth binary sequence x4(i), the fifth binary sequence x5(i), and the sixth binary sequence x6(i). The cyclic shift indexes v4 and v5 associated with the fourth binary sequence x4(i) and the fifth binary sequence x5(i) can have a total of 63 values. The cyclic shift index v6 ​​associated with the sixth binary sequence x6(i) can have a total of 7 values. Therefore, theoretically, the third wireless signal sequence S v、3 The maximum number of distinguishable identification indexes based on (k) can be 63×63×7=16129. v、3 (k) can have up to 63 cyclically distinct sequences.

[0147] In one embodiment of the communication system, the value of the discrimination index v may be selected between 0 and Ξ. If v=999, then g=333 based on Equation 7.

number

[0333] Ω , g2=0, u=0. In this case, the circular shift indices associated with the fourth binary sequence x4(i), the fifth binary sequence x5(i), and the sixth binary sequence x6(i) are v4=0, v5= Ω and

number

number

[0148] In Equation 8, if Ξ is set to 1008, Ω may be determined to be 48. If the value of Ξ is set to twice 1008 (i.e., 2016), Ω may be determined to be 48. Based on the value of Ω determined in accordance with Equation 8, the values ​​of cyclic shift indexes v4, v5, and v6 may be determined. In Equations 7 and 8, 441 may correspond to a first reference value. Setting the first reference value to 441 is merely an example for convenience of explanation, and the fourth embodiment of the wireless signal generation method is not limited thereto.

[0149] The basic radio signal sequence S generated based on Equation 1 v (k) and the third radio signal sequence S generated based on Equation 7. v、3(k) can be compared identically or similarly to Table 5. [Table 5]

[0150] Referring to Table 5, the basic radio signal sequence S v The number N of subcarriers onto which (k) is mapped after modulation may be 127, and the third radio signal sequence S v、3 The number N of subcarriers onto which (k) is mapped after modulation may be 126. That is, the third radio signal sequence S generated by the fourth embodiment of the radio signal generation method v、3 (k) is the basic radio signal sequence S v (k) or can support approximately 1.72 times more identification indexes while using the same frequency resource. v、3 (k) is generated based on a linearly distinguishable sequence, so that the third radio signal sequence S v、3 The correlation characteristics and variability between the synchronization signal pairs generated based on (k) can be maintained.

[0151] <Fifth embodiment of wireless signal generation method> In one embodiment of the communication system, the first communication node can generate a fourth radio signal according to a fifth embodiment of the radio signal generation method. In the fifth embodiment of the radio signal generation method, the fourth radio signal can be generated based on one or more fourth radio signal sequences. The one or more first radio signal sequences can be generated based on one or more binary sequences. The one or more fourth radio signal sequences can be generated based on S v、4 It can be expressed as (k).

[0152] In one embodiment of the communication system, a fourth radio signal sequence S v、4 The fourth radio signal sequence S(k) may be generated based on the seventh binary sequence x7(i), the eighth binary sequence x8(i), and the ninth binary sequence x9(i). v、4(k) may be generated based on the second intermediate sequence ζ(m), which may be defined based on the seventh binary sequence x7(i), the eighth binary sequence x8(i), and the ninth binary sequence x9(i). The seventh binary sequence x7(i), the eighth binary sequence x8(i), and the ninth binary sequence x9(i) may correspond to PN sequences. For example, the fourth wireless signal sequence S v、4 (k) may be defined the same as or similar to Equation 9.

number

[0153] In Equation 9, the value of N can be 126 or 127. When N is 126, it can be considered that one of the 127 subcarriers (e.g., the center subcarrier) in the first subcarrier group described with reference to FIG. 5a is excluded from the indexing. When N is 127, it can be considered that the center subcarrier among the 127 subcarriers in the first subcarrier group is included in the indexing, and the value assigned to the center subcarrier is 0.

[0154] The seventh binary sequence x7(i) and the eighth binary sequence x8(i) may be defined based on different generator polynomials having a maximum degree of 6. The seventh binary sequence x7(i) may be determined based on the seventh recurrence formula, x7(i+6) = [x7(i+1) + x7(i+0)]2. The eighth binary sequence x8(i) may be determined based on the eighth recurrence formula, x8(i+6) = [x8(i+5) + x8(i+2) + x8(i+1) + x8(i+0)]2. The ninth binary sequence x9(i) may be defined based on a generator polynomial having a maximum degree of 3. The ninth binary sequence x9(i) may be determined based on the ninth recurrence formula, x9(i+3) = [x9(i+2) + x9(i+0)]2. The recurrence formula and numbers shown in Equation 9 are merely examples for the convenience of explanation, and the fifth embodiment of the wireless signal generation method is not limited thereto. For example, the seventh binary sequence x7(i), the eighth binary sequence x8(i), and the ninth binary sequence x9(i) can be generated in various ways other than the recurrence formula shown in Equation 9.

[0155] In Equation 9, the formula "ζ" is used to calculate the second intermediate sequence ζ(m) based on the seventh binary sequence x7(i), the eighth binary sequence x8(i), and the ninth binary sequence x9(i). v (m)=1-2[x7([m+v7] 63 )+x8([m+v8] 63 )+x9([m+v9]7)]2" can correspond to BPSK operation. v、4 (k) First Group S v、4 (N / 2-1-k) is a 'S' based on the second intermediate sequence ζ(m). v、4 (N / 2-1-k)=ζ v (k)” as the fourth radio signal sequence S v、4 (k) Second Group S v、4 (k+N / 2) is a 'S' based on the second intermediate sequence ζ(m). v、4 (k+N / 2)=ζ v (k)” as the fourth radio signal sequence S v、4 (k) 2nd group 2nd group S v、4(k+N / 2) is the first group S v、4 This corresponds to a symmetric repetition of (N / 2-1-k). Thus, a fourth radio signal sequence S including the first and second groups is v、4 (k) can have the value of real number 1 or -1.

[0156] In Equation 9, Ω can be calculated based on Ξ, which means the number of distinguishable identification index v values. The fourth wireless signal sequence S generated by Equation 9 is v、4 Depending on (k), a total of Ξ identification indexes can be identified, where Ω can be calculated based on Ξ in the same or similar manner as in Equation 8.

[0157] The fourth radio signal sequence S generated based on Equation 9 v、4 (k) is the third radio signal sequence S described with reference to Table 5. v、3 That is, the fourth wireless signal sequence S generated by the fifth embodiment of the wireless signal generation method can have the same or similar advantages as the fourth wireless signal sequence S (k). v、4 (k) is the basic radio signal sequence S v (k) can be one less than (k), or can support approximately 1.72 times more identification indexes while using the same frequency resources.

[0158] In addition, the fourth radio signal sequence S v、4 (k) is defined as in Equation 9, the fourth radio signal sequence S v、4 (k) time domain signal s v、4 [n] can be determined as in Equation 10.

number

[0159] The fourth radio signal sequence S expressed as Equation 10 v、4 (k) time domain signal s v、4 Referring to [n], signal s v、4[n] may have only real components in the time domain. The first communication node transmitting the fourth wireless signal may transmit only the real part when transmitting the fourth wireless signal. This may reduce the transmission complexity of the fourth wireless signal.

[0160] According to an embodiment of a method and apparatus for transmitting and receiving a wireless signal in a communication system, the performance of an estimation operation or an identification operation based on a wireless signal transmitted and received between a transmitting node and a receiving node can be improved. The wireless signal according to an embodiment of a method and apparatus for transmitting and receiving a wireless signal in a communication system can support more identification index divisions while using the same frequency resource. The wireless signal according to an embodiment of a method and apparatus for transmitting and receiving a wireless signal in a communication system can reduce the computational complexity for an estimation operation or an identification operation. The wireless signal according to an embodiment of a method and apparatus for transmitting and receiving a wireless signal in a communication system can have lower transmission complexity while using the same frequency resource.

[0161] However, the effects that can be achieved by the embodiments of the method and apparatus for transmitting and receiving a wireless signal in a communication system are not limited to those mentioned above, and other effects not mentioned can be clearly understood by a person with ordinary skill in the art to which the present disclosure pertains from the configurations described in the specification of the present disclosure.

[0162] The operations of the methods according to the embodiments of the present disclosure may be embodied as a computer-readable program or code stored in a computer-readable recording medium. The computer-readable recording medium may include any type of storage device that stores information readable by a computer system. The computer-readable recording medium may also be distributed among computer systems connected via a network, allowing the computer-readable program or code to be stored and executed in a distributed manner.

[0163] The computer-readable recording medium may also include a hardware device specially configured to store and execute program instructions, such as a ROM, RAM, flash memory, etc. The program instructions may include not only machine code, such as produced by a compiler, but also high-level language code that can be executed by a computer using an interpreter, etc.

[0164] Some aspects of the present disclosure have been described in terms of devices, but they can also be described in terms of corresponding methods, where blocks or devices correspond to method steps or features of method steps. Similarly, aspects described in terms of methods can also be described in terms of corresponding blocks or items or features of corresponding devices. Some or all of the method steps can be performed by (or using) a hardware device, such as, for example, a microprocessor, a programmable computer, or an electronic circuit. In some embodiments, at least one or more of the most important method steps can be performed by such a device.

[0165] In embodiments, a programmable logic device (e.g., a field programmable gate array) may be used to perform some or all of the functions of the methods described herein. In embodiments, a field programmable gate array may operate in conjunction with a microprocessor to perform one of the methods described herein. In general, it is preferred that the methods be performed by some hardware device.

[0166] Although the present disclosure has been described above with reference to preferred embodiments, those skilled in the art will understand that the present disclosure can be modified and changed in various ways without departing from the spirit and scope of the present disclosure as set forth in the claims below.

Claims

1. 1. A method of operating a first communication node in a communication system, comprising: generating first and second binary sequences consisting of 2N elements; generating a first intermediate sequence consisting of 2N elements based on the first and second binary sequences and a Binary Phase Shift Keying (BPSK) operation; generating a first signal sequence consisting of N elements based on operations on the 2N elements that make up the first intermediate sequence; mapping first modulation symbols generated by modulating the first signal sequence to N subcarriers; transmitting a first signal composed of the mapped first modulation symbols; the first and second binary sequences are generated based on a generator polynomial having a maximum degree (p+1) and a first identifier for the first communication node; The p is a natural number, and the N is (2 ｐ is a natural number having a value of −1, A method of operating a first communication node.

2. The step of generating the first intermediate sequence comprises: generating first and second cyclic shift indices based on the first identifier; applying the first cyclic shift index to the first binary sequence; applying the second cyclic shift index to the second binary sequence; performing the BPSK operation on the sum of the first and second binary sequences to which the first and second cyclic shift indexes have been applied; obtaining the first intermediate sequence corresponding to the result of the BPSK operation; A method for operating a first communication node according to claim 1.

3. generating the first signal sequence multiplying a (2k-1)-th element of the 2N elements constituting the first intermediate sequence by a first coefficient that is a real number; multiplying a 2k-th element of the 2N elements constituting the first intermediate sequence by a second coefficient that is a pure imaginary number; performing a sum operation on the (2k-1)th element multiplied by the first coefficient and the 2kth element multiplied by the second coefficient; obtaining the k-th element of the first signal sequence based on a result of the sum operation; The k is a natural number greater than or equal to 1 and less than or equal to N. A method for operating a first communication node according to claim 1.

4. generating the first signal sequence multiplying a (2k-1)-th element of the 2N elements constituting the first intermediate sequence by a first coefficient that is a real number; multiplying a 2k-th element of the 2N elements constituting the first intermediate sequence by a second coefficient that is a pure imaginary number; performing a sum operation on the (2k-1)th element multiplied by the first coefficient and the 2kth element multiplied by the second coefficient; performing a rotational transformation operation by a first angle on a complex plane on the result of the sum operation; obtaining the k-th element of the first signal sequence based on the result of the rotational transformation operation; The k is a natural number greater than or equal to 1 and less than or equal to N. A method for operating a first communication node according to claim 1.

5. the first angle is one of π / 4, −π / 4, 3π / 4, or −3π / 4; A method for operating a first communication node according to claim 4.

6. The first signal has a maximum of (2N+1) ２ Supporting distinct values ​​of A method for operating a first communication node according to claim 1.

7. 1. A method of operating a first communication node in a communication system, comprising: generating first and second binary sequences consisting of (N / 2) elements and a third binary sequence consisting of M elements; generating a first intermediate sequence consisting of (N / 2) elements based on the first to third binary sequences and a binary phase shift keying (BPSK) operation; generating first and second element groups each consisting of (N / 2) elements based on the first intermediate sequence; generating a first signal sequence consisting of N elements based on the first and second groups of elements; mapping first modulation symbols generated by modulating the first signal sequence to N subcarriers; transmitting a first signal composed of the mapped first modulation symbols; The first and second binary sequences are generated based on a generator polynomial having a maximum degree (p-1), and first to third cyclic shift indexes determined based on a first identifier for the first communication node are applied to the first to third binary sequences, respectively, where p is a natural number equal to or greater than 2, and N is a number greater than or equal to (2 ｐ -2), and M is a natural number having a value equal to or less than (N / 2). A method of operating a first communication node.

8. The step of generating the first intermediate sequence comprises: determining the first to third cyclic shift indexes based on the first identifier; applying the first cyclic shift index to the first binary sequence; applying the second cyclic shift index to the second binary sequence; applying the third cyclic shift index to the third binary sequence; performing the BPSK operation on the sum of the first to third binary sequences to which the first to third cyclic shift indexes have been applied; obtaining the first intermediate sequence corresponding to the result of the BPSK operation; A method for operating a first communication node according to claim 7.

9. The step of determining the first to third cyclic shift indexes includes: determining a first variable g based on the value of the first identifier; determining a second variable Ω based on the number of values ​​that the first identifier can have; determining the first to third cyclic shift indexes based on the first variable g, the second variable Ω, and a first reference value t and one or more modulo operations; The g, Ω, and t are natural numbers. A method for operating a first communication node according to claim 8.

10. the second cyclic shift index is determined based on a t-modulo operation and an Ω-modulo operation on the first variable g. A method for operating a first communication node according to claim 9.

11. The first signal supports up to (M×(N / 2)×(N / 2)) distinct values ​​for the first identifier. A method for operating a first communication node according to claim 8.

12. The (N / 2) elements constituting the first element group are represented by a k-th element, and the (N / 2) elements constituting the second element group are represented by an (N / 2+k)-th element, The step of generating the first and second element groups includes: obtaining the k-th element of the first element group based on a k-th element of the (N / 2) elements constituting the first intermediate sequence; obtaining the (N / 2+k)th element of the second element group based on the kth element of the (N / 2) elements constituting the first intermediate sequence; the N elements constituting the first signal sequence are configured to include the (N / 2) elements constituting the first element group and the (N / 2) elements constituting the second element group; The k is a natural number greater than or equal to 1 and less than or equal to (N / 2). A method for operating a first communication node according to claim 7.

13. The (N / 2) elements constituting the first element group are represented by an (N / 2+1-k)th element, and the (N / 2) elements constituting the second element group are represented by an (N / 2+k)th element, The step of generating the first and second element groups includes: obtaining the (N / 2+1-k)th element of the first element group based on a kth element of the (N / 2) elements constituting the first intermediate sequence; obtaining the (N / 2+k)th element of the second element group based on the kth element of the (N / 2) elements constituting the first intermediate sequence; the N elements constituting the first signal sequence are configured to include the (N / 2) elements constituting the first element group and the (N / 2) elements constituting the second element group; The k is a natural number greater than or equal to 1 and less than or equal to (N / 2). A method for operating a first communication node according to claim 7.

14. The first modulation symbols mapped to the N subcarriers have a central symmetric structure centered on a first reference subcarrier of the N subcarriers. A method for operating a first communication node according to claim 13.

15. the first signal has only real components in the time domain; A method for operating a first communication node according to claim 13.

16. A first communication node in a communication system, a processor, The processor may further configure the first communication node to: generating first and second binary sequences consisting of (N / 2) elements, and a third binary sequence consisting of M elements; generating a first intermediate sequence consisting of (N / 2) elements based on the first to third binary sequences and a binary phase shift keying (BPSK) operation; generating first and second element groups each consisting of (N / 2) elements based on the first intermediate sequence; generating a first signal sequence consisting of N elements based on the first and second groups of elements; mapping first modulation symbols generated by modulating the first signal sequence onto N subcarriers; and operative to cause a first signal comprising the mapped first modulation symbols to be transmitted; The first and second binary sequences are generated based on a generator polynomial having a maximum degree (p-1), and first to third cyclic shift indexes determined based on a first identifier for the first communication node are applied to the first to third binary sequences, respectively, where p is a natural number equal to or greater than 2, and N is a number greater than or equal to (2 ｐ -2), and M is a natural number having a value equal to or less than (N / 2). A first communication node.

17. When generating the first intermediate sequence, the processor may cause the first communication node to: determining the first to third cyclic shift indexes based on the first identifier; applying the first circular shift index to the first binary sequence; applying the second circular shift index to the second binary sequence; applying the third cyclic shift index to the third binary sequence; performing the BPSK operation on the sum of the first to third binary sequences to which the first to third cyclic shift indexes have been applied; and further operable to cause obtaining the first intermediate sequence corresponding to the result of the BPSK operation. The first communication node according to claim 16.

18. When determining the first to third cyclic shift indexes, the processor may cause the first communication node to: determining a first variable g based on the value of the first identifier; determining a second variable Ω based on the number of values ​​that the first identifier can have; and further operative to cause determining the first, second, and third cyclic shift indexes based on the first variable g, the second variable Ω, and a first reference value t and one or more modulo operations; The g, Ω, and t are natural numbers.

18. The first communication node according to claim 17.

19. the second cyclic shift index is determined based on a t-modulo operation and an Ω-modulo operation on the first variable g.

19. The first communication node according to claim 18.

20. The first signal supports up to (M×(N / 2)×(N / 2)) distinct values ​​for the first identifier.

20. The first communication node of claim 19.

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