Fiber-coupled terahertz transceiver system

Abstract

Transmission networks, network elements, and methods of use are described herein, including a transmitter comprising a client-side input, a transmitter circuit, and antennas. The client-side input is configured to receive baseband signals having client data encoded therein. The transmitter circuit is configured to receive baseband signals from the client-side input and generate antenna feed signals based on the baseband signals. The antennas are configured to receive antenna feed signals from the transmitter circuit, generate radiated signals based on the antenna feed signals, and combine the radiated signals within a hollow waveguide. Each of the radiated signals is a radiated electromagnetic wave configured for coherent detection and has a frequency within the range of 300 gigahertz (GHz) to 10 terahertz (THz).

Description

Technology Field

[0001] [Cross-reference to related applications]

[0002] The present application claims the benefit of priority under 35 USC 119(e) with respect to the following applications, which are: a provisional application filed on June 4, 2024 and identified by U.S. Serial No. 63 / 655,823; a provisional application filed on June 10, 2024 and identified by U.S. Serial No. 63 / 658,162; a provisional application filed on June 10, 2024 and identified by U.S. Serial No. 63 / 658,176; a provisional application filed on June 18, 2024 and identified by U.S. Serial No. 63 / 661,437; and a provisional application filed on July 2, 2024 and identified by U.S. Serial No. 63 / 666,886. A provisional application filed on April 5, 2024 and identified by U.S. Serial No. 63 / 575,162; and a provisional application filed on October 27, 2023 and identified by U.S. Serial No. 63 / 593,874, the entire contents of all these provisional applications are thereby incorporated herein by reference. Background Technology

[0003] Optical networking is a means of communication that uses optically encoded signals to transmit information in various types of telecommunication networks, including local-area networks (LANs) or wide-area networks (WANs) within a limited range. Optical networking is a form of optical communication that generally relies on optical amplifiers, lasers or LEDs, and wavelength-division multiplexing (WDM) technology to transmit large amounts of data over fiber optic cables. Because optical networking can achieve extremely high bandwidths, it is a key technology enabling the Internet and telecommunication networks that transmit the vast majority of information between all people and machines. However, the further development and optimization of optical networking systems face several limiting factors, specifically power dissipation, thermal requirements, and mechanical tolerances.

[0004] Optical components generate photons by exciting electrons within a gain medium, and these photons are emitted when the electrons return to lower energy levels. Despite efforts to improve efficiency, optical components generate a certain amount of heat during the electron excitation process; this heat generation is referred to as power dissipation. Excessive power dissipation can cause thermal management issues and affect the performance and durability of optical components.

[0005] Optical components are sensitive to temperature fluctuations and often require lower operating temperatures than pure electronic components to maintain optimal performance. Rising temperatures can lead to increased signal noise, degraded signal quality, and a shortened service life of optical components. Therefore, optical components often require cooling systems (e.g., heat sinks, fans, or thermoelectric elements) to dissipate excess heat and keep them within a safe temperature range.

[0006] Because optical networking systems typically operate at micrometer wavelengths, they require extreme precision in component manufacturing, assembly, and alignment. Even minute deviations from the required mechanical tolerances can lead to signal degradation, loss, or the introduction of optical crosstalk, negatively impacting network performance. Achieving and maintaining these necessary mechanical tolerances requires advanced manufacturing techniques and stringent quality control measures. means of solving the problem

[0007] Transport networks, network elements, and methods of use are disclosed herein. Problems regarding power dissipation, thermal requirements, and mechanical tolerances are addressed through a terahertz (THM) RF transmission system in which radio frequency (RF) signals are coupled to hollow waveguides for transmission.

[0008] From the perspective of power dissipation, RF transceivers lack optical components, thereby eliminating the power requirements associated with activating optical components and generating photons. Furthermore, transmitting RF signals in the THz frequency band involves longer wavelengths than transmitting optical signals in higher frequency bands, which means less energy is required to generate and modulate the signals. Finally, since RF transceivers operate entirely within the electrical domain, no optoelectric conversion is required. Consequently, power dissipation is reduced in fiber-coupled THz RF transceiver systems. Because RF transceivers do not contain optical components sensitive to temperature fluctuations, they also lead to a reduction in thermal requirements. As a result, no temperature control or DC (direct current) bias control is required. Moreover, thanks to the reduced thermal requirements, RF transceivers can be more easily integrated into existing processes or technologies. From the perspective of mechanical tolerances, antennas do not require the precise alignment performed by optical systems (i.e., coupling RF signals into hollow waveguides requires less precision than coupling optical signals into hollow waveguides). Furthermore, operating in the THz frequency band implies that the wavelengths of the signals being transmitted are much longer, which also contributes to the relaxation of mechanical tolerances. Finally, from the perspective of spectral efficiency, RF systems are generally more spectrally efficient than optical systems, thereby enabling an increase in throughput.

[0009] In one embodiment, the present disclosure comprises a transmitter, wherein the transmitter comprises: a client-side input configured to receive one or more baseband signals having client data encoded therein; a transmitter circuit configured to receive one or more baseband signals from the client-side input and generate one or more antenna feed signals based on one or more baseband signals; and one or more antennas configured to receive one or more antenna feed signals from the transmitter circuit and generate one or more radiated signals based on one or more antenna feed signals and couple one or more radiated signals to a hollow waveguide, wherein each of the one or more radiated signals is a radiated electromagnetic wave configured for coherent detection and has a frequency in the range of 300 gigahertz (GHz) to 10 terahertz (THz).

[0010] In another aspect, the present disclosure comprises a receiver, wherein the receiver comprises: one or more antennas configured to detect one or more radiated signals received from a hollow waveguide and to generate one or more antenna output signals based on one or more radiated signals—each of the one or more radiated signals being a radiated electromagnetic wave configured for coherent detection and having a frequency in the range of 300 GHz (Gigahertz) to 10 THz (Terahertz) and having client data encoded therein—; a receiver circuit configured to receive one or more antenna output signals from one or more antennas and to generate one or more baseband signals based on one or more antenna output signals; and a client-side output configured to receive one or more baseband signals from the receiver circuit and to transmit one or more baseband signals.

[0011] In another aspect, the present disclosure comprises a transport network, wherein the transport network comprises: one or more hollow waveguides; a transmitter; and a receiver, wherein the transmitter comprises: a client-side input configured to receive one or more first baseband signals having client data encoded therein; a transmitter circuit configured to receive one or more first baseband signals from the client-side input and generate one or more antenna feed signals based on one or more first baseband signals; and one or more first antennas configured to receive one or more antenna feed signals from the transmitter circuit and generate one or more radiation signals based on one or more antenna feed signals, and to couple one or more radiation signals to at least one of one or more hollow waveguides—each of the one or more radiation signals being a radiated electromagnetic wave configured for coherent detection and having a frequency within the range of 300 GHz to 10 THz—and the receiver comprises one or more second antennas configured to detect one or more radiation signals received from at least one of one or more hollow waveguides and generate one or more antenna output signals based on one or more radiation signals; A receiver circuit configured to receive one or more antenna output signals from one or more second antennas and generate one or more second baseband signals based on one or more antenna output signals, wherein one or more second baseband signals have client data; and a client-side output configured to receive one or more second baseband signals from the receiver circuit and transmit one or more second baseband signals.

[0012] In another aspect, the present disclosure comprises a transceiver, wherein the transceiver comprises: a transmitter; and a receiver, wherein the transmitter comprises: a client-side input configured to receive one or more first baseband signals having first client data; and a transmitter circuit configured to receive one or more first baseband signals from the client-side input and generate one or more antenna feed signals based on one or more first baseband signals. and comprising one or more first antennas configured to receive one or more antenna feed signals from a transmitter circuit and generate one or more first radiation signals based on one or more antenna feed signals, and to couple one or more first radiation signals to a first hollow waveguide - each of the one or more first radiation signals is a radiated electromagnetic wave configured for coherent detection and has a first frequency within the range of 300 GHz to 10 THz - and the receiver comprises: one or more second antennas configured to detect one or more second radiation signals received from one of a first hollow waveguide and a second hollow waveguide and to generate one or more antenna output signals based on one or more second radiation signals - each of the one or more second radiation signals is a radiated electromagnetic wave configured for coherent detection and has a second frequency within the range of 300 GHz to 10 THz and has second client data -; a receiver circuit configured to receive one or more antenna output signals from one or more second antennas and to generate one or more second baseband signals based on one or more antenna output signals; and includes a client-side output configured to receive one or more second baseband signals from a receiver circuit and transmit one or more second baseband signals. Brief explanation of the drawing

[0013] The accompanying drawings, which are included in and constitute part of this specification, illustrate one or more of the embodiments described herein and describe such embodiments together with the description. The drawings are not intended to be drawn to scale, and certain features and views of the drawings may be shown exaggerated, to scale, or schematically for clarity and conciseness. Not all components may be given a reference numeral in every drawing. Similar reference numbers in the drawings may indicate and refer to the same or similar elements or functions. In the drawings: Figure 1 is a diagrammatic view of the electromagnetic (EM) spectrum. FIG. 2 is a block diagram of an exemplary implementation of a transmission network configured according to the present disclosure. FIG. 3a is a cross-sectional view of an exemplary implementation of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows. FIG. 3b is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, wherein the first hollow waveguide has no optional dielectric layer. FIG. 3c is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, wherein the first hollow waveguide has no optional support layer. FIG. 3d is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, wherein the first hollow waveguide has no optional dielectric layer and no optional support layer. FIG. 3e is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a photonic-bandgap fiber. FIG. 3f is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, wherein the first hollow waveguide has a hollow waveguide core having an elliptical cross section. FIG. 3g is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the hollow waveguide core of the first hollow waveguide has a rectangular cross-section. FIG. 3h is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the hollow waveguide core of the first hollow waveguide has a square cross-section. FIG. 3i is a cross-sectional view of another exemplary implementation of the first hollow waveguide shown in FIG. 2, taken along line 3-3' in the direction of the arrow, where the hollow waveguide core of the first hollow waveguide has a cross-shaped cross section. FIG. 3j is a cross-sectional view of another exemplary implementation of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a solid rod fiber. FIG. 3k is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a microstructured optical fiber. FIG. 3L is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a porous fiber. FIG. 3m is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a suspended porous-core fiber. FIG. 3n is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a suspended slotted core fiber. FIG. 3o is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a hollow-core bandgap fiber. FIG. 3p is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a hollow-core tube fiber. FIG. 3q is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a hollow core fiber having a negative curvature. FIG. 3r is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a hollow core fiber based on anti-resonances and inhibited coupling. FIG. 3s is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a hollow-core nested anti-resonant nodeless fiber. FIG. 3t is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a 3D printed hollow core fiber based on anti-resonances and coupling suppression. FIG. 3u is a cross-sectional view of another exemplary embodiment of the first hollow waveguide shown in FIG. 2, taken along line 3-3' and in the direction of the arrows, where the first hollow waveguide is a Bragg fiber. FIG. 4a is a block diagram of an exemplary implementation of the first transmitter shown in FIG. 2. FIG. 4b is a block diagram of another exemplary implementation of the first transmitter shown in FIG. 2, wherein the first transmitter includes a serializer. FIG. 4c is a block diagram of another exemplary implementation of the first transmitter shown in FIG. 2, wherein the first transmitter includes a deserializer. FIG. 4d is a block diagram of an exemplary implementation of the transmitter circuit shown in FIG. 4a. FIG. 4e is a block diagram of another exemplary implementation of the transmitter circuit shown in FIG. 4a, wherein the transmitter circuit includes a combiner. FIG. 4f is a block diagram of another exemplary implementation of the first transmitter shown in FIG. 2. FIG. 4g is a block diagram of another exemplary implementation of the first transmitter shown in FIG. 2. FIG. 5a is a block diagram of an exemplary implementation of the first receiver shown in FIG. 2. FIG. 5b is a block diagram of another exemplary implementation of the first receiver shown in FIG. 2, wherein the first receiver includes a deserializer. FIG. 5c is a block diagram of another exemplary implementation of the first transmitter shown in FIG. 2, wherein the first transmitter includes a serializer. FIG. 5d is a block diagram of an exemplary implementation of the receiver circuit shown in FIG. 5a. FIG. 5e is a block diagram of another exemplary implementation of the receiver circuit shown in FIG. 5a, wherein the receiver circuit includes a splitter. FIG. 5f is a block diagram of another exemplary implementation of the first receiver shown in FIG. 2. FIG. 5g is a block diagram of another exemplary implementation of the first receiver shown in FIG. 2. FIG. 6a is a block diagram of an exemplary implementation of the transceiver shown in FIG. 2. FIG. 6b is a block diagram of another exemplary implementation of the transceiver shown in FIG. 2. FIG. 7 is a schematic diagram of a folded modulator configured according to the present disclosure. FIG. 8 is a schematic diagram of a rectifying detector configured according to the present disclosure. FIG. 9a is a side view of an exemplary embodiment of an antenna configured according to the present disclosure to generate circularly polarized signals. FIG. 9b is a side view of another exemplary implementation of the antenna shown in FIG. 9a. FIG. 10 is a perspective view of another exemplary embodiment of the antenna shown in FIG. 9a, where the antenna is a bifilar helix antenna. FIG. 11 is a perspective view of another exemplary embodiment of the bipillar helix antenna shown in FIG. 10, wherein the bipillar helix antenna is enclosed within a conductive cone. FIG. 12 is a partial cross-sectional view of the bipillar helix antenna shown in FIG. 11, taken from line 12-12' and in the direction of the arrows. FIG. 13 is a diagram of the electric field produced by a bipilar helix antenna enclosed within the conductive cone shown in FIG. 12. FIG. 14 is a diagram of the radiation pattern of a bipilar helix antenna enclosed within the conductive cone shown in FIG. 12. FIG. 15 is a side view of an exemplary embodiment of a non-uniform bipilar helix antenna configured according to the present disclosure. FIG. 16 is a side view of another exemplary implementation of a non-uniform bipilar helix antenna. Figure 17 is a graph of polarization discrimination of the non-uniform bipilar helix antenna shown in Figure 15. Figure 18 is a graph of the polarization distinction of the non-uniform bipilar helix antenna shown in Figure 16. FIG. 19 is a side view of another exemplary implementation of a non-uniform bipilar helix antenna. FIG. 20 is a side view of another exemplary implementation of a non-uniform bipilar helix antenna. FIG. 21 is a diagram illustrating an exemplary implementation of a differential waveguide probe antenna configured according to the present disclosure. FIG. 22a is a partial cross-sectional view of the differential waveguide probe antenna shown in FIG. 21, taken from line 22-22' and in the direction of the arrows. FIG. 22b is another partial cross-sectional view of the differential waveguide probe antenna shown in FIG. 22a, taken from line 23-23' and in the direction of the arrows. FIG. 22c is another partial cross-sectional view of the differential waveguide probe antenna shown in FIG. 22b, taken from line 24-24' and in the direction of the arrows. FIG. 22d is a graph of the polarization distinction of the differential waveguide probe antenna shown in FIG. 21. FIG. 23 is an illustration of an exemplary implementation of a differential tapered antenna configured according to the present disclosure. FIG. 24a is a partial cross-sectional view of the differential tapered antenna shown in FIG. 23, taken from line 27-27' and in the direction of the arrows. FIG. 24b is another partial cross-sectional view of the differential tapered antenna shown in FIG. 24a, taken from line 28-28' and in the direction of the arrows. FIG. 24c is a graph of the polarization distinction of the differential tapered antenna shown in FIG. 23. FIG. 25 is an illustration of an exemplary implementation of a differential microstrip patch antenna configured according to the present disclosure. FIG. 26 is a diagram illustrating an exemplary implementation of a single-ended waveguide probe antenna configured according to the present disclosure. FIG. 27a is a cross-sectional view of the single-ended waveguide probe antenna shown in FIG. 26, taken along line 55-55' and in the direction of the arrows. FIG. 27b is another cross-sectional view of the single-ended waveguide probe antenna shown in FIG. 26, taken along line 56-56' and in the direction of the arrows. FIG. 27c is a partial cross-sectional view of the single-ended waveguide probe antenna shown in FIG. 27b, taken along line 57-57' and in the direction of the arrows. FIG. 28 is a diagram illustrating an exemplary implementation of a slot antenna configured according to the present disclosure. FIG. 29a is a cross-sectional view of the slot antenna shown in FIG. 28, taken along line 59-59' and in the direction of the arrows. FIG. 29b is a partial cross-sectional view of the slot antenna shown in FIG. 29a, taken along line 60-60' and in the direction of the arrows. FIG. 29c is another partial cross-sectional view of the slot antenna shown in FIG. 29a, taken along lines 61-61' and in the direction of the arrows. FIG. 30a is a cross-sectional view of another implementation of the slot antenna shown in FIG. 28, taken along line 59-59' and in the direction of the arrows, where the slot antenna is a double slot antenna. FIG. 30b is a partial cross-sectional view of the slot antenna shown in FIG. 30a, taken along line 63-63' and in the direction of the arrows. FIG. 30c is another partial cross-sectional view of the slot antenna shown in FIG. 30a, taken along line 64-64' and in the direction of the arrows. FIG. 31 is a diagram of another exemplary implementation of a transmission network configured according to the present disclosure. FIG. 32a is a diagram of an exemplary implementation of the transmitter shown in FIG. 31. FIG. 32b is a diagram of an exemplary implementation of the receiver shown in FIG. 31. FIG. 33 is a diagram of an exemplary implementation of the antenna array shown in FIG. 31. FIG. 34 is a diagram of another exemplary implementation of a transmission network configured according to the present disclosure. FIG. 35a is a diagram of an exemplary implementation of the antenna array shown in FIG. 34, wherein the first antenna, second antenna, third antenna, and fourth antenna are arranged in an nxm grid pattern. FIG. 35b is a diagram of another exemplary implementation of the antenna array shown in FIG. 34, where the first antenna, second antenna, third antenna, and fourth antenna are arranged in a 1 x m grid pattern. FIG. 36 is an illustration of a method using the transmission network illustrated in FIG. 31. FIG. 37a is an illustration of an exemplary implementation of a dual-polarization network element configured according to the present disclosure. FIG. 37b is a diagram of another exemplary implementation of a dual-polarization network element configured according to the present disclosure. FIG. 38 is an illustration of a dual-polarized signal according to the present disclosure. FIG. 39 is an illustration of an exemplary implementation of a dual-polarization transmission network configured according to the present disclosure, wherein the dual-polarization transmission network includes a dual-polarization RF antenna. FIG. 40 is a diagram illustrating another exemplary implementation of a dual-polarization transmission network configured according to the present disclosure, wherein the dual-polarization transmission network includes a first RF antenna pair and a second RF antenna pair. FIG. 41 is a diagram illustrating another exemplary implementation of a dual-polarization transmission network configured according to the present disclosure, wherein the dual-polarization transmission network comprises a plurality of first RF antennas and a plurality of second RF antennas. FIG. 42 is a diagram of an exemplary implementation of the first modulator shown in FIG. 37a. FIG. 43 is a diagram of an exemplary implementation of the first demodulator shown in FIG. 37b. FIG. 44 is a diagram illustrating another exemplary implementation of a dual-polarization network element configured according to the present disclosure, wherein the dual-polarization network element includes an equalizer. FIG. 45 is an illustration of a method of use according to the present disclosure. FIG. 46a is a diagram illustrating another exemplary implementation of a network element configured according to the present disclosure, wherein the network element is configured to perform a direct conversion from a first modulation format of a first electrical signal to a second modulation format of a second electrical signal in the THz frequency band. FIG. 46b is a diagram illustrating another exemplary implementation of a network element configured according to the present disclosure, wherein the network element is configured to perform a direct conversion from a first modulation format to a second modulation format in the THz frequency band and includes an RF antenna. FIG. 47a is a diagram of an exemplary implementation of the demodulator shown in FIG. 46a. FIG. 47b is a diagram illustrating another exemplary embodiment of a demodulator configured according to the present disclosure, wherein the demodulator includes a clock-and-data-recovery circuit (CDR). FIG. 48 is a diagram of an exemplary implementation of the first phase demodulator shown in FIG. 47a. FIG. 49 is a diagram of an exemplary implementation of the first amplitude demodulator shown in FIG. 47a. FIG. 50a is a diagram of an exemplary implementation of the modulator shown in FIG. 46a and FIG. 46b. FIG. 50b is a diagram of another exemplary implementation of the modulator shown in FIG. 46a and FIG. 46b, wherein the modulator includes a local oscillator (LO) generator. FIG. 51 is an illustration of an exemplary implementation of a method for performing direct modulation from a first modulation format to a second modulation format in an electrical signal within the THz frequency band. FIG. 52 is a diagram illustrating an exemplary implementation of the first phase modulator shown in FIG. 50a and FIG. 50b, wherein the first phase modulator includes a crossbar switch. FIG. 53a is a diagram of an exemplary implementation of the first amplitude modulator shown in FIG. 50a and FIG. 50b, wherein the first amplitude modulator includes a PI-type switched attenuator. FIG. 53b is a diagram of another exemplary implementation of the first amplitude modulator shown in FIG. 50a and FIG. 50b, wherein the first amplitude modulator includes a T-type switched attenuator. FIG. 53c is a diagram of another exemplary implementation of the first amplitude modulator shown in FIG. 50a and FIG. 50b, wherein the first amplitude modulator includes a bridged T-type switched attenuator. FIG. 54 is a diagram of another exemplary embodiment of a transceiver configured according to the present disclosure. FIG. 55 is a diagram of another exemplary embodiment of a transceiver configured according to the present disclosure. FIG. 56 is a diagram of another exemplary embodiment of a transceiver configured according to the present disclosure. FIG. 57 is a diagram of another exemplary embodiment of a transmitter configured according to the present disclosure. FIG. 58 is a diagram of another exemplary embodiment of a receiver configured according to the present disclosure. FIG. 59 is a diagram of another exemplary embodiment of a transmitter configured according to the present disclosure. FIG. 60 is a diagram of another exemplary embodiment of a transmitter configured according to the present disclosure. FIG. 61 is an illustration of an exemplary implementation of a differential circuit configured according to the present disclosure. FIG. 62 is a diagram of another exemplary implementation of the differential circuit shown in FIG. 61. FIG. 63 is a diagram of another exemplary implementation of the differential circuit shown in FIG. 61. FIG. 64 is a diagram of another exemplary embodiment of an antenna array configured according to the present disclosure. FIG. 65 is a perspective view of an exemplary embodiment of an electromagnetic absorber used and configured according to the present disclosure. FIG. 66 is a cross-sectional view of another exemplary embodiment of an electromagnetic absorber constructed according to the present disclosure. FIG. 67 is a cross-sectional view of another exemplary embodiment of an electromagnetic absorber constructed according to the present disclosure. FIG. 68 is a cross-sectional view of another exemplary embodiment of an electromagnetic absorber constructed according to the present disclosure. FIG. 69 is a diagram of another exemplary embodiment of an electromagnetic absorber constructed according to the present disclosure. FIG. 70 is a flowchart of an exemplary implementation of a process according to the present disclosure. FIG. 71 is a flowchart of another exemplary implementation of a process according to the present disclosure. FIG. 72 is a process flowchart of an exemplary implementation of a configuration process configured according to the present disclosure. Specific details for implementing the invention

[0014] Refer to the attached drawings for the following detailed description. Identical reference numbers in different drawings may identify identical or similar elements.

[0015] As used herein, the terms “comprises,” “comprising,” “includes,” “including,” “has,” “having,” or any other variations thereof are intended to cover non-exclusive inclusions. For example, a process, method, article, or device comprising a list of elements is not necessarily limited to these elements alone and may include other elements not explicitly enumerated or inherent in such process, method, article, or device. Also, unless explicitly stated otherwise, “or” refers to an inclusive or rather than an exclusive or. For example, condition A or B is satisfied by any one of the following: A is true (or exists) and B is false (or does not exist); A is false (or does not exist) and B is true (or exists); and both A and B are true (or exist).

[0016] Additionally, the use of singular expressions (“a” or “an”) is adopted to describe the elements and components of the implementations of this specification. This is done merely for convenience and to provide a general meaning of the concept of the invention. This description should be read as containing one or more things, and the singular also includes the plural unless otherwise evident. As used herein, the term “implementation” is synonymous with the term “example.”

[0017] Furthermore, the use of the term "plurality" is intended to mean "more than one" unless explicitly stated otherwise.

[0018] As used herein, modifiers such as “substantially,” “about,” and “approximately,” and combinations and variations thereof, are intended to include not only the exact quantity or value they modify, but also some minute deviations from such quantity or value that may be attributed to, for example, manufacturing tolerances, measurement errors, wear and damage, stresses applied to various parts, and combinations thereof.

[0019] The use of the terms "at least one" or "one or more" shall be understood to include not only one but any quantity greater than one. Furthermore, the use of the phrase "at least one of X, V, and Z" shall be understood to include X alone, V alone, and Z alone, as well as any combination of X, V, and Z.

[0020] The use of ordinal terms (i.e., “first,” “second,” “third,” “fourth,” etc.) is intended only to distinguish two or more items and, unless explicitly stated otherwise, is not intended to imply any order or sequence between items, the importance of one item to another, or any order of addition.

[0021] Finally, as used herein, any reference to “one embodiment” or “implementation” means that a specific element, feature, structure, or characteristic described in association with the implementation is included in at least one implementation. Not all instances of the phrase “in one embodiment” appearing in various places herein refer to the same implementation.

[0022] As used herein, unless the context clearly indicates otherwise, all numeric values ​​or ranges include fractions of values, integers within these ranges, and fractions of integers within these ranges. Thus, for illustrative purposes, a reference to a numeric range such as 1-10 includes 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, as well as 1.1, 1.2, 1.3, 1.4, 1.5, etc., and all other values. Accordingly, a reference to the range 1-50 includes values ​​up to 50, including 1, 2, 3, 4, 5, 6, 7, 8, 9, 10, 11, 12, 13, 14, 15, 16, 17, 18, 19, 20, etc., as well as values ​​1.1, 1.2, 1.3, 1.4, 1.5, etc., 2.1, 2.2, 2.3, 2.4, 2.5, etc., and all other values. A reference to a series of ranges includes ranges formed by combining boundary values ​​of different ranges within the said series of ranges. Accordingly, for example, a reference to a series of ranges such as 1-10, 10-20, 20-30, 30-40, 40-50, 50-60, 60-75, 75-100, 100-150, 150-200, 200-250, 250-300, 300-400, 400-500, 500-750, and 750-1,000 includes, for example, the ranges 1-20, 10-50, 50-100, 100-500, and 500-1,000.

[0023] As used herein, “circuit” may refer to analog and / or digital components, or one or more appropriately programmed processors (e.g., microprocessors) and associated hardware and software, or hardwired logic. Additionally, “components” may perform one or more functions. The term “component” may include hardware such as a processor (e.g., a microprocessor), a combination of hardware and software, and / or similar. Software may include one or more processor-executable instructions that cause one or more processors to perform a specified function when executed by one or more processors. It should be understood that the algorithms described herein may be stored in one or more non-transient memories. Exemplary non-transient memories may include random access memory, read-only memory, flash memory, and / or similar ones. Such non-transient memories may be electrically based, optically based, and / or similar.

[0024] As used herein, "mode" refers to the intrinsic distribution of electric and magnetic fields repeating along the length of a hollow waveguide, wherein electromagnetic energy can be transported by and through the hollow waveguide. "Single mode" refers to a hollow waveguide designed to carry only one mode of electromagnetic waves. This is achieved by having a narrow core diameter that allows only one mode of light to propagate at a time. Conversely, "multimode" refers to a hollow waveguide designed to carry multiple modes of electromagnetic waves simultaneously. This is made possible by a larger core diameter that allows multiple modes to propagate.

[0025] As used herein, "Amplitude Modulation (AM)" refers to a form of signal modulation in which data is encoded into the amplitude of a carrier signal.

[0026] As used herein, "Amplitude-Shift Keying (ASK)" refers to a form of AM in which digital data is encoded into the amplitude of a carrier signal, and each symbol (i.e., representing one or more data bits) is transmitted by transmitting a carrier wave of fixed amplitude at a fixed frequency for a specific period.

[0027] As used herein, “Phase-Shift Keying (PSK)” is a form of signal modulation in which signal data is encoded into the phase of a carrier signal having a constant frequency. “Quadrature PSK” is a form of PSK that modulates two data bits (i.e., 00, 01, 10, or 11) at a time by selecting one of four possible carrier phase shifts (i.e., 0°, 90°, 180°, or 270°).

[0028] As used herein, "Pulse-Amplitude Modulation (PAM)" refers to a form of AM in which a data signal is encoded in the amplitudes of a series of carrier signal pulses. "PAM4" refers to a form of PAM in which a data signal is encoded in the amplitudes of a series of carrier signal pulses, wherein the amplitudes of the carrier signal pulses may be one of four discrete values ​​(i.e., 0, 1, 2, or 3) and each carrier signal pulse represents two data bits (i.e., 00, 01, 10, or 11).

[0029] As used herein, “Non-Return-to-Zero (NRZ)” refers to a form of signal modulation in which a binary data signal is encoded into a carrier signal such that 1s are represented by a first valid condition (e.g., positive voltage) and 0s are represented by a second valid condition (e.g., negative voltage). “Non-Return-to-Zero Inverted (NRZI)” refers to a form of signal modulation in which a data bit is represented by the presence or absence of a transition at a clock boundary.

[0030] As used herein, “Quadrature Amplitude Modulation (QAM)” refers to a form of AM in which two analog message signals or two digital bit streams are encoded into the amplitudes of two carriers using ASK or AM, and the two carrier signals are out of phase with each other by 90°. “QAM16” refers to a form of QAM in which one of the carrier signals may exist in one of 16 discrete states (i.e., symbols) representing four data bits (i.e., 0000 to 1111) by having one of 16 different amplitude and phase levels.

[0031] As used herein, "Trellis Coded Modulation (TCM)" refers to a form of signal modulation in which a binary data signal is encoded into the phase of a carrier signal of constant amplitude. The transmitted signal is generated by convolution encoding the binary data signal and mapping the result to a signal constellation diagram.

[0032] As used herein, "Rayleigh range" refers to the distance along the direction of propagation from the waist of the beam to the point where the cross-sectional area is doubled.

[0033] As used herein, "hollow waveguide" refers to a structure that guides waves by restricting energy transmission in a specific direction. In the context of this disclosure, "hollow waveguide" may refer to an optical fiber having a waveguide core operable to propagate RF signals in the THz frequency band, or a routed waveguide operable to propagate RF signals in the THz frequency band.

[0034] As used herein, "diameter" refers to a straight line passing through the center of an object or figure and connecting both ends. In some embodiments, the object or figure has a circular or elliptical shape.

[0035] As used herein, “data” refers to quantities, characters, or symbols on which operations are performed by a computer. Data may be recorded on non-transient computer-readable media, such as random access memory and / or read-only memory. Random access memory and / or read-only memory may be implemented on semiconductor, magnetic, optical, or mechanical recording media. An example of data is client data, for example, data provided by a client in connection with telecommunications services and / or storage services.

[0036] Now, referring to the drawings, particularly FIG. 1, an illustration of an electromagnetic (EM) spectrum (100) according to the present disclosure is shown. The present disclosure relates to network elements communicating using radiation signals comprising radiated electromagnetic waves coupled within hollow waveguides. The radiation signals described herein generally have a transmission frequency (i.e., frequencies of 0.1 THz to 10 THz corresponding to wavelengths of 3 millimeters (mm) to 30 micrometers (μm)), referred to as the terahertz (THz) frequency band (104). However, in some embodiments described herein, the transmission frequency of the radiation signals is in the range of 300 gigahertz (GHz) to 10 THz. The radiation signals described herein are generally configured for coherent detection and generally have a bandwidth corresponding to a range of 10% to 40% of the transmission frequency.

[0037] Now, referring to FIG. 2, a block diagram of an exemplary implementation of a transport network (200) (hereinafter referred to as the "transport network" (200)) configured according to the present disclosure is shown. The transport network (200) is described as comprising a plurality of network elements (204a-n) (hereinafter referred to as "network elements (204)") (e.g., the first network element (204a), the second network element (204b), the third network element (204c), and the fourth network element (204d) shown in FIG. 2). Although only four of the network elements (204) are shown in FIG. 2 for illustrative purposes, it should be understood that the transport network (200) may include a predetermined number of network elements (204), which may be more or fewer than four.

[0038] The transmission network (200) may additionally include one or more hollow waveguides (208a-n) (hereinafter, "hollow waveguides (208)") (e.g., the first hollow waveguide (208a), the second hollow waveguide (208b), the third hollow waveguide (208c), and the fourth hollow waveguide (208d) shown in FIG. 2). Although only four of the hollow waveguides (208) are shown in FIG. 2 for illustrative purposes, it should be understood that the transmission network (200) may include a predetermined number of hollow waveguides (208), which may be more or fewer than four.

[0039] Radiated signals transmitted from a first network element (204a) to a fourth network element (204d) or vice versa within a transmission network (200) may travel along (1) a first path formed by a first hollow waveguide (208a), a second network element (204b), and a second hollow waveguide (208b), or (2) a second path formed by a third hollow waveguide (208c), a third network element (204c), and a fourth hollow waveguide (208d).

[0040] In some embodiments, each of the hollow waveguides (208) is configured to support the propagation of radiated signals in only one direction. However, in other embodiments, one or more of the hollow waveguides (208) may be configured to support the propagation of radiated signals in multiple directions (i.e., two opposite directions). In embodiments where one or more of the hollow waveguides (208) are configured to support the propagation of radiated signals in multiple directions, a first radiated signal propagating through the hollow waveguide (208) in a first direction may be distinguished from a second radiated signal propagating through the hollow waveguide (208) in a second direction opposite to the first direction by being assigned a different polarization, frequency, etc. In some such embodiments, one or more circulators may be included to achieve such distinction.

[0041] Each of the network elements (204) is operable to transmit radiation signals including radiating electromagnetic waves having client data encoded therein through hollow waveguides (208) (e.g., a first transmitter (212a) and a second transmitter (212b) shown in FIG. 2), a receiver (216) operable to receive radiation signals including radiating electromagnetic waves having client data encoded therein through hollow waveguides (208) (e.g., a first receiver (216a) and a second receiver (216b) shown in FIG. 2), and / or to transmit first radiation signals including first radiating electromagnetic waves having first client data encoded therein through specific waveguides among the hollow waveguides (208) and / or to receive second radiation signals including second radiating electromagnetic waves having second client data encoded therein through other hollow waveguides among the hollow waveguides (208). It may include one or more of the transceivers (220) (e.g., the first transceiver (220a) shown in FIG. 2 and the second transceiver (220b) shown in FIG. 6b).

[0042] Each of the network elements (204) may further include a control module (224) (e.g., a first control module (224a), a second control module (224b), a third control module (224c), and a fourth control module (224d) as illustrated in FIG. 2) (collectively, "control modules (224)") which is operable to regulate one or more operation parameters of the network element (204) to which the control module (224) is coupled.

[0043] In some implementations, one or more of the network elements (204) may communicate with each other through a communication network (228). The communication network (228) may allow bidirectional communication of information and / or data between one or more of the network elements (204) of the transmission network (200). The communication network (228) may interface with one or more of the network elements (204) in various ways. For example, in some implementations, the communication network (228) may interface by optical and / or electronic interfaces and / or may use multiple network topologies and / or protocols, including but not limited to Ethernet, TCP / IP, circuit-switched paths, combinations thereof, and / or similar ones. The communication network (228) may utilize various network protocols to allow bidirectional interface and / or communication of data and / or information between one or more of the network elements (204).

[0044] The communication network (228) can be almost any type of network. For example, in some implementations, the communication network (228) can be a type of internet network (e.g., it can exist in a TCP / IP-based network). In one implementation, the communication network (228) is the internet. However, it should be noted that the communication network (228) can be almost any type of network and can be implemented as the World Wide Web (i.e., the internet), a local area network (LAN), a wide area network (WAN), a metropolitan network, a wireless network, a cellular network, a Bluetooth network, a Global System for Mobile Communications (GSM) network, a code division multiple access (CDMA) network, a 3G network, a 4G network, an LTE network, a 5G network, a satellite network, a radio network, an optical network, a cable network, a public switched telephone network, an Ethernet network, combinations thereof, and / or similar.

[0045] If the communication network (228) is the Internet, the main user interface of the transmission network (200) may be written in a hypertext markup language, JavaScript, or similar language and may be provided through a series of web pages of a company or entity or private internal web pages that are accessible to the user. It should be noted that the main user interface of the transmission network (200) may be another type of interface, including, but not limited to, Windows-based applications, tablet-based applications, mobile web interfaces, VR-based applications, applications running on mobile devices, and / or similar ones. In one implementation, the communication network (228) may be connected to one or more of the network elements (204).

[0046] The predetermined number of devices and / or networks shown in FIG. 2 are provided for exemplary purposes. In practice, there may be additional devices and / or networks, fewer devices and / or networks, different devices and / or networks, or devices and / or networks arranged differently from those shown in FIG. 2. Furthermore, two or more of the devices shown in FIG. 2 may be implemented within a single device, or the single device shown in FIG. 2 may be implemented as a plurality of distributed devices. Additionally or alternatively, one or more of the devices of the transmission network (200) may perform one or more functions described as being performed by another or more of the devices of the transmission network (200).

[0047] Network elements (204) can take many different forms. For example, network elements (204) may be integrated circuits (ICs). In this example, network elements (204) (e.g., ICs) may communicate via signals containing radiated electromagnetic waves with client data encoded therein through hollow waveguides (208) without requiring electrical data buses. In other implementations, network elements (204) may be integrated into components within a data center to establish communication between components within the data center via signals containing radiated electromagnetic waves propagated through hollow waveguides (208) and containing client data encoded therein, such components being, for example, servers, routers, switches, firewalls, storage systems, application delivery controllers, and / or similar. Accordingly, hollow waveguides (208) may extend from one integrated circuit to another integrated circuit, or from one component to another component, and this may be implemented in various ways such as IC-to-IC communications, printed circuit board (PCB)-to-PCB communications, component-to-component communications, and / or combinations thereof. In the example of PCB-to-PCB communications, network elements (204) may each include a PCB.

[0048] Now, referring to FIGS. 3a through 3h and FIGS. 4a through 4l, cross-sectional views of various exemplary embodiments of the first hollow waveguide (208a) shown in FIG. 2 are shown, taken along line 3-3' in the direction of the arrows. However, it should be understood that the description referring to FIGS. 3a through 3h and FIGS. 4a through 4l may be applicable to any of the hollow waveguides (208) described herein. In the embodiments shown in FIGS. 3a through 3h and FIGS. 4a through 4l, the first hollow waveguide (208a) is a hollow fiber. However, it should be understood that in other embodiments, the first hollow waveguide (208a) may be another type of hollow waveguide, such as, for example, a substrate-integrated waveguide.

[0049] The first hollow waveguide (208a) (and thus each of the hollow waveguides (208)) generally comprises a hollow waveguide core (304) and a tubular sidewall (306) having an inner surface (312) that limits the hollow waveguide core (304) in some embodiments or simply surrounds the hollow waveguide core (304) in other embodiments.

[0050] Generally, the hollow waveguide core (304) may be composed of any material capable of propagating radiated electromagnetic waves in the THz frequency band (104), or in some embodiments in the range of 300 GHz to 10 THz. More specifically, the hollow waveguide core (304) may be composed of any material having low absorption loss (i.e., absorption loss within the range of 1 dB / km to 10,000 dB / km) in the THz frequency band (104), or in some embodiments in the range of 300 GHz to 10 THz.

[0051] In some embodiments, the hollow waveguide core (304) may be composed of a polymer (e.g., cyclo olefin polymer (COP), cyclic olefin co-polymer (COC), polytetrafluoroethylene (PTFE), high-density polyethylene (HDPE), polymethylpentene (PMP), polypropylene (PP), polystyrene, polycarbonate, poly(methyl methacrylate) (PMMA), Picarin, or UV resin) or glass (e.g., silica glass, crown glass, or borosilicate glass).

[0052] In other embodiments, the hollow waveguide core (304) may be composed of gas, vacuum, or a porous material (i.e., a material having a porosity in the range of 25% to 99%). In such embodiments, the hollow waveguide core (304) may have a refractive index in the range of, for example, 1.0 to 1.4. As will be discussed in more detail below, the hollow waveguide core (304) has a refractive index Can have.

[0053] In some embodiments, the hollow waveguide core (304) may have a cross section configured to support the propagation of radiated signals having only a single polarization at a given time. However, in other embodiments, the hollow waveguide core (304) may have a cross section configured to support the propagation of radiated signals having multiple polarizations at a given time. In either case, the hollow waveguide core (304) may have a cross section configured to support the propagation of radiated signals having one or more linear polarizations or one or more circular polarizations.

[0054] In some implementations, the hollow waveguide core (304) may have a cross section configured to support the propagation of radiated signals having only a single mode at a given time. However, in other implementations, the hollow waveguide core (304) may have a cross section configured to support the propagation of radiated signals having multiple modes at a given time.

[0055] The tubular sidewall (306) of the first hollow waveguide (208a) (and thus, each of the hollow waveguides (208)) may include a conductive layer (316) (illustrated in FIG. 3a to 3i) surrounding the hollow waveguide core (304), a dielectric layer (308) (illustrated in FIG. 3a, 3c, and FIG. 3f to 3i) optionally disposed between the hollow waveguide core (304) and the conductive layer (316), and a support layer (320) (illustrated in FIG. 3a, 3b, and FIG. 3e to 3i) optionally surrounding the conductive layer (316).

[0056] In some embodiments, the tubular sidewall (306) of the first hollow waveguide (208a) (and, thus, each of the hollow waveguides (208)) may include a plurality of conductive layers (316) interleaved with a plurality of dielectric layers (308).

[0057] In some embodiments, the tubular sidewall (306) of the first hollow waveguide (208a) (and, thus, each of the hollow waveguides (208)) may further include one or more strength members (not shown) (hereinafter, "strength members") surrounding a conductive layer (316) configured to enhance the resilience of the first hollow waveguide (208a). In such embodiments, a support layer (320) may surround the strength members.

[0058] Generally, the conductive layer (316) has the refractive index of the hollow waveguide core (304) (i.e., Refractive index greater than ) It may be composed of any material having. More specifically, the conductive layer (316) may be composed of a non-oxidizing metallic material (e.g., silver, gold, or indium tin oxide (ITO)). Providing the conductive layer (316) with a refractive index greater than that of the hollow waveguide core (304) is the effective refractive index of the first hollow waveguide (208a). This can cause an increase, thereby causing more radiation signals to be confined and propagated within the hollow waveguide core (304).

[0059] Generally, in implementations where the dielectric layer (308) is disposed between the conductive layer (316) and the hollow waveguide core (304), the dielectric layer (308) has the refractive index of the hollow waveguide core (304) (i.e., Refractive index greater than ) It may be composed of any material having. More specifically, the dielectric layer (308) may be composed of a polymer (e.g., cycloolefin polymer (COP), cyclic olefin copolymer (COC), polytetrafluoroethylene (PTFE), high-density polyethylene (HDPE), polymethylpentene (PMP), polypropylene (PP), polystyrene, polycarbonate, poly(methyl methacrylate) (PMMA), picarin, or ultraviolet (UV) resin) or glass (e.g., silica glass, crown glass, or borosilicate glass), but particularly in its implementation, the refractive index of the hollow waveguide core (304) (i.e., Refractive index greater than ) It may be composed of a material having. Providing a dielectric layer (308) having a refractive index greater than the refractive index of the hollow waveguide core (304) is the effective refractive index of the first hollow waveguide (208a). This can cause an increase, thereby causing more radiation signals to be confined and propagated within the hollow waveguide core (304).

[0060] The support layer (320) may be configured to shield the inner layers of the first hollow waveguide (208a) (and, therefore, any of the hollow waveguides (208)) from external environmental factors, provide flexibility to the first hollow waveguide (208a), and / or improve the tensile strength of the first hollow waveguide (208a). In some embodiments, the support layer (320) may be composed of polymer materials such as, for example, acrylate polymer or polyimide.

[0061] In some embodiments, the cross-section of the hollow waveguide core (304) is circular in shape (i.e., equal diameter along both the x-axis and y-axis). It may have (as shown in FIGS. 3a to 3d). In some such implementations, the diameter of the hollow waveguide core (304) The diameter may be 30 μm to 6 mm. In some such embodiments, the diameter of the hollow waveguide core (304) The diameter may be 30 μm to 3 mm. In at least one such embodiment, the diameter of the hollow waveguide core (304) It can be 1mm.

[0062] In some embodiments, as illustrated in FIG. 3e, the first hollow waveguide (208a) may be a photonic-bandgap fiber comprising a plurality of periodically spaced air channels (324) (hereinafter, "air channels (324)") throughout the conductive layer (316).

[0063] In other implementations, for example, the cross-section of the hollow waveguide core (304) is elliptical (i.e., a first diameter along the x-axis). and the second diameter along the y-axis having, where the first diameter is not the same as the second diameter) (illustrated in FIG. 3f), rectangular shape (illustrated in FIG. 3g) (i.e., the first length along the x-axis and the second length along the y-axis It has, and the first length is not the same as the second length), a square shape (i.e., equal length along both the x-axis and the y-axis) Having (as shown in Fig. 3h), or a cross shape (i.e., equal length along both the x-axis and y-axis) It can have (as illustrated in Fig. 3i).

[0064] In other embodiments, the first hollow waveguide (208a) (and, therefore, any of the hollow waveguides (208)) is, for example, a solid rod fiber (illustrated in FIG. 3j), a microstructured optical fiber (illustrated in FIG. 3k), a porous fiber (illustrated in FIG. 3l), a suspended porous-core fiber (illustrated in FIG. 3m), a suspended slotted core fiber (illustrated in FIG. 3n), a hollow-core bandgap fiber (illustrated in FIG. 3o), a hollow-core tube fiber (illustrated in FIG. 3p), a hollow-core fiber with negative curvature (illustrated in FIG. 3q), a hollow-core fiber based on anti-resonances and suppressed coupling. It can be implemented as an inhibited coupling fiber (shown in Fig. 3r), a hollow-core nested anti-resonant nodeless fiber (shown in Fig. 3s), a 3D-printed hollow-core fiber based on anti-resonants and inhibited coupling (shown in Fig. 3t), or a Bragg fiber (shown in Fig. 3u).

[0065] Now, referring to FIG. 4a, a block diagram of an exemplary implementation of the first transmitter (212a) shown in FIG. 2 is shown. However, it should be understood that the description of any specific transmitter (212) may be applicable to any of the transmitters (212) described herein. A first transmitter (212a) (and thus each of the transmitters (212)) generally comprises a client-side input (400) configured to receive one or more baseband signals (404) (hereinafter “baseband signals (404)”) having client data encoded therein from one or more external components (e.g., a control module (224)), a transmitter circuit (408) configured to receive baseband signals (404) from the client-side input (400) and generate one or more antenna feed signals (412) (hereinafter “antenna feed signals (412)”) based on the baseband signals (404), and receiving antenna feed signals (412) from the transmitter circuit (408), generating one or more radiation signals (420) (hereinafter “radiation signals (420)”) based on the antenna feed signals (412), and the radiation signals (420) to the first hollow It includes one or more first antennas (416) configured to be coupled within the waveguide (208a).

[0066] In some implementations, the client-side input (400) is a pair of inputs configured to receive a differential signal. In some such implementations, the client-side input (400) may be an LVDS link configured to receive low voltage differential signaling (LVDS) signals, and the baseband signals (404) may be LVDS signals representing client data.

[0067] In some embodiments, antenna feed signals (412) are provided to the first antenna (416) over one or more transmission lines (not shown) (hereinafter, "transmission lines"), each of which has two or more conductors (not shown) (hereinafter, "conductors"). In some embodiments, the transmission lines have a first transmission loss, and the first hollow waveguide (208a) has a second transmission loss smaller than the first transmission loss. In some embodiments, the second transmission loss is in the range of 0.001 to 20.00 decibels (dB) per meter (m) per terabits (Tb) per second (s).

[0068] In some embodiments, as illustrated in FIG. 4a, the client-side input (400), the transmitter circuit (408), and the first antennas (416) may each be placed on a substrate (424). However, in other embodiments, one or more of the client-side input (400), the transmitter circuit (408), and the first antennas (416) may be placed on a first substrate (not shown), and one or more of the client-side input (400), the transmitter circuit (408), and the first antennas (416) may not be placed on the first substrate. For example, one or more of the client-side input (400), the transmitter circuit (408), and the first antennas (416) may be placed on a second substrate (not shown). In such embodiments, the first substrate and the second substrate may be arranged in a stacked array.

[0069] In some embodiments, the substrate (424) may have a plurality of layers (not shown). In such embodiments, one or more of the client-side input (400), the transmitter circuit (408), and the first antennas (416) may be placed on a first layer (not shown), and one or more of the client-side input (400), the transmitter circuit (408), and the first antennas (416) may be placed on a second layer (not shown).

[0070] In some embodiments, one or more of the client-side input (400), transmitter circuit (408), and first antennas (416) may be integrated within a monolithic semiconductor die (not shown). In some embodiments, one or more of the client-side input (400), transmitter circuit (408), and first antennas (416) may be implemented using one or more of CMOS (complementary metal-oxide semiconductor) technology, SiGe (silicon-germanium) semiconductor technology, and III-V compound semiconductor technology.

[0071] In some implementations, the baseband signals (404) are digital bitstreams. In some implementations, client data may be encoded in the baseband signals (404) using an encoding protocol that complies with one or more requirements of return-to-zero (RZ) code, non-return-to-zero (NRZ) code, pulse-amplitude modulation (PAM), and quadrature-amplitude modulation (QAM). In some implementations, client data may be encoded in the radiated signals (420) using an encoding protocol that complies with one or more requirements of RZ, NRZ, quadrature phase-shift keying (QPSK), QAM, trellis coded modulation (TCM), and BCH (Bose-Chaudhuri-Hocquenghem) code.

[0072] In some embodiments, the radiated signals (420) include a first complementary radiated signal (not shown) having a first polarization and a second complementary radiated signal (not shown) having a second polarization different from the first polarization. In such embodiments, the first antennas (416) may be configured to generate radiated signals (420) including the first complementary radiated signal and the second complementary radiated signal based on antenna feed signals (412). The first polarization and the second polarization may be orthogonal to each other.

[0073] In some embodiments, the first polarization and the second polarization may each be linear polarizations. In such embodiments, the first antennas (416) may include one or more of a differential waveguide probe antenna, a differential tapered antenna, and a differential patch antenna. In other embodiments, the first polarization and the second polarization may each be circular polarizations. In such embodiments, the first antennas (416) may include one or more of a helix antenna and a spiral antenna. It should be understood that any of the signals described herein may be single-ended signals or differential signals.

[0074] In some embodiments, the radiated signals (420) include a first complementary radiated signal (not shown) having a first polarization and a second complementary radiated signal (not shown) having a second polarization different from the first polarization, and the first antennas (416) are further configured to combine the first complementary radiated signal and the second complementary radiated signal within a first hollow waveguide (208a) such that the first complementary radiated signal and the second complementary radiated signal interact within the first hollow waveguide (208a) to form a combined radiated signal (not shown) having a third polarization different from the first polarization and the second polarization. In such embodiments, the first antennas (416) may include an antenna array.

[0075] Now, referring to FIG. 4b, in some implementations, the first transmitter (212a) (and, therefore, any of the transmitters (212)) further comprises a first serializer (426) configured to receive a plurality of parallel baseband signals (428a-n) (hereinafter, "parallel baseband signals (428)") and combine the parallel baseband signals (428) to become a serial baseband signal (i.e., baseband signals (404)). In such implementations, the client-side input (400) may be configured to receive the baseband signals (404) from the first serializer (426). In some such implementations, combining parallel baseband signals (428) to become baseband signals (404) utilizes at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM).

[0076] Now, referring to FIG. 4c, in some implementations, the first transmitter (212a) (and thus any of the transmitters (212)) further includes a first deserializer (432) configured to receive a serial baseband signal (i.e., baseband signals (404)) and split the baseband signals (404) into parallel baseband signals (428). In such implementations, the client-side input (400) may be configured to receive the parallel baseband signals (428) from the first deserializer (432). In some such implementations, splitting the baseband signals (404) into parallel baseband signals (428) utilizes at least one of PDM, TDM, and WDM.

[0077] Now, referring to FIG. 4d, an exemplary implementation of the transmitter circuit (408) illustrated in FIG. 4a through 4c is shown. In some embodiments, the transmitter circuit (408) comprises one or more local oscillators (436a-n) (hereinafter "LO (436)") configured to generate one or more carrier signals (440) (hereinafter "carrier signals (440)") having a baseband frequency lower than the transmission frequency, one or more modulation circuits (444) (hereinafter "modulator (444)") configured to generate one or more modulated signals (448) (hereinafter "modulated signals (448)") by receiving baseband signals (404) from a client-side input (400) and carrier signals (440) from the LO (436) and modulating the baseband signals (404) onto the carrier signals (440), and receiving the modulated signals (448) from the modulator (444) and up-converting the modulated signals (448) (i.e., modulating It includes one or more up-conversion circuits (452) (hereinafter, "up-conversion circuits (452)") configured to generate antenna feed signals (412) by raising the frequency of the signals (448) from the baseband frequency to the transmission frequency.

[0078] Now, referring to FIG. 4e, in an implementation configured such that a client-side input (400) receives parallel baseband signals (428), a transmitter circuit (408) may be configured to receive parallel baseband signals (428) from the client-side input (400). In such an implementation, a modulator (444) may be configured to receive parallel baseband signals (428) from the client-side input (400) and carrier signals (440) from the first LO (436), and to generate modulation signals (448) by modulating the parallel baseband signals (428) onto the carrier signals (440). In such implementations, the upconverter (452) may be configured to receive modulation signals (448) from the modulator (444) and upconvert the modulation signals (448) to generate one or more upconverted signals (460) (hereinafter referred to as "upconverted signals (460)").

[0079] In some embodiments, the transmitter circuit (408) may further include a combiner (456) configured to receive up-converted signals (460) from an up-converter (452) and combine the up-converted signals (460) to become antenna feed signals (412). However, in other embodiments, the first antennas (416) may be configured to receive antenna feed signals (412) from an up-converter (452), generate radiation signals (420) based on the antenna feed signals (412), and combine the radiation signals (420) within a first hollow waveguide (208a) such that the radiation signals (420) interact within the first hollow waveguide (208a) to form a combined radiation signal (not shown).

[0080] In some implementations, at least one of PDM, TDM, and WDM is utilized to combine the radiated signals (420) within the first hollow waveguide (208a), wherein the radiated signals (420) interact within the first hollow waveguide (208a) to form a combined radiated signal.

[0081] Now, referring to FIG. 4f, a block diagram of another exemplary implementation of the first transmitter (212a) shown in FIG. 2 is shown. However, it should be understood that the description of any specific transmitter among the transmitters (212) may apply to any transmitter among the transmitters (212) described herein.

[0082] In the implementation illustrated in FIG. 4f, the first transmitter (212a) comprises a client-side input (400) configured to receive baseband signals (404) from one or more external components (e.g., a control module (224)) and transmit the baseband signals (404) to a transmitter circuit (408); a transmitter circuit (408) configured to receive baseband signals (404) from the client-side input (400), generate antenna feed signals (412) based on the baseband signals (404), and transmit the antenna feed signals (412) to an RF interface (464); an RF interface (464) configured to receive antenna feed signals (412) from the transmitter circuit (408) and transmit the antenna feed signals (412); and a digital enhancement and control unit (468) configured to provide digital control and / or processing functions for one or more of the components of the first transmitter (212a).

[0083] In the implementation illustrated in FIG. 4f, the transmitter circuit (408) includes one or more modulation blocks (444a) (hereinafter, "modulation blocks (444a)"), a frequency synthesizer (472) including a phase-locked loop (PLL) (476) and a first LO (436a), a second LO (436b), a first frequency mixer (480a), a second frequency mixer (480b), a first amplifier (484a), and a second amplifier (484b).

[0084] The modulation block (444a) may be configured to receive baseband signals (404) from a client-side input (400) and to encode the baseband signals (404) into a format suitable for modulation onto a carrier signal. In some implementations, the modulation block (444a) may include one or more digital-to-analog converters (DACs), one or more serializers / deserializers (SerDes), one or more folded modulators (700) (shown in FIG. 7), and / or circuits operable to encode the baseband signals (404) into a modulation format such as, for example, AM, ASK, PSK, QAM, QAM16, or variations thereof. In some implementations, the modulation block (444a) may include circuits operable to perform forward error correction (FEC). The modulation block (444a) may be further configured to transmit encoded input signals having data encoded therein to the second frequency mixer (480b).

[0085] In some implementations, the modulation block (444a) is configured to simply receive baseband signals (404) (i.e., baseband signals (404) previously encoded in a modulation format) from a client-side input (400) and transmit the baseband signals (404) to a second frequency mixer (480b).

[0086] The second LO (436b) may be configured to generate second carrier signals having a continuous waveform (e.g., a sine wave waveform) having a predetermined frequency (i.e., baseband (BB) frequency). In some embodiments, the predetermined frequency (i.e., BB frequency) of the second carrier signals is in the RF band (i.e., in the range of 30 Hz to 300 GHz). In some embodiments, the predetermined frequency (i.e., BB frequency) of the second carrier signals is in the range of 1 MHz to 300 GHz. In some embodiments, the predetermined frequency (i.e., BB frequency) of the second carrier signals is in the range of 5 GHz to 30 GHz. The second LO (436b) may be further configured to transmit the second carrier signals to a second frequency mixer (480b).

[0087] The second frequency mixer (480b) may be configured to receive baseband signals encoded from the modulation block (444a), receive second carrier signals from the second LO (436b), upconvert the encoded baseband signals into second carrier signals to produce first modulation signals having client data encoded therein and also having a predetermined frequency (i.e., BB frequency) of the second carrier signals, and transmit the first modulation signals to the third amplifier (484c).

[0088] The third amplifier (484c) may be configured to receive first modulation signals from the second frequency mixer (480b), adjust the amplitude of the first modulation signals so that the amplified first modulation signals can drive the first frequency mixer (480a), and transmit the amplified first modulation signals to the first frequency mixer (480a).

[0089] The frequency synthesizer (472) (i.e., the first LO (436a) and PLL (476)) may be configured to generate first carrier signals having a continuous waveform (e.g., a sine wave waveform) having a predetermined frequency (e.g., within the THz frequency band (104), or in some implementations, within the range of 300 GHz to 10 THz). In some implementations, the predetermined frequency of the first carrier signals is in the range of 30 GHz to 300 GHz. In some such implementations, the predetermined frequency of the first carrier signals is 240 GHz. In other implementations, the predetermined frequency of the first carrier signals is in the range of 300 GHz to 3 THz. The frequency synthesizer (472) may be further configured to transmit the first carrier signals to a second amplifier (484b).

[0090] The second amplifier (484b) may be configured to receive first carrier signals from the first LO (436a), adjust the amplitude of the first carrier signals to generate amplified carrier signals capable of driving the first frequency mixer (480a), and transmit the amplified carrier signals to the first frequency mixer (480a).

[0091] The first frequency mixer (480a) may be configured to receive carrier signals amplified from the second amplifier (484b), receive first modulation signals amplified from the third amplifier (484c), upconvert the amplified first modulation signals into amplified carrier signals to have client data encoded therein, and also produce second modulation signals having a predetermined frequency of the amplified carrier signals (i.e., in the THz frequency band (104), or in some implementations, in the range of 300 GHz to 10 THz), and transmit the second modulation signals to the first amplifier (484a).

[0092] The first amplifier (484a) may be configured to receive second modulation signals from the first frequency mixer (480a), adjust the amplitude of the second modulation signals so that the amplified second modulation signals can be transmitted by the RF interface (464), and transmit the amplified second modulation signals to the RF interface (464). The first amplifier (484a) may be configured to generate the amplified second modulation signals to have power within the range of, for example, 0.05 watts (W) to 0.4 W.

[0093] The RF interface (464) may be configured to receive amplified second modulation signals having client data encoded therein from the first amplifier (484a) and to transmit the amplified second modulation signals as antenna feed signals (412) (i.e., having client data encoded therein) in a predetermined frequency range (e.g., the THz frequency band (104) or, in some implementations, the range from 300 GHz to 10 THz). In some implementations, the RF interface (464) may be electrically connected to one of the first antennas (416) and configured to transmit the antenna feed signals (412) to the first antenna (416). However, in other implementations, the first antennas (416) may be included instead of the RF interface (464).

[0094] Now, referring to FIG. 4g, a block diagram of another exemplary implementation of the first transmitter (212a) shown in FIG. 2 is shown. In the implementation illustrated in FIG. 5b, the first transmitter (212a) comprises a plurality of inputs including an I-BB client-side input (400a) and a Q-BB client-side input (400b) configured to receive in-phase (I)-BB baseband signals (404a) and quadrature (Q)-BB baseband signals (404b) respectively from one or more external components (e.g., a control module (224)), an LO input (400c) configured to receive one or more carrier signals (488) (hereinafter, "carrier signals (488)") from an external LO, a transmitter circuit (408) configured to generate antenna feed signals (412) based on the I-BB baseband signals (404a), Q-BB baseband signals (404b), and carrier signals (488), and an RF configured to transmit the antenna feed signals (412). Includes an interface (464).

[0095] In the implementation illustrated in FIG. 4g, the transmitter circuit (408) includes a balancing unit (Balun) (492), a third frequency mixer (480c), a fourth frequency mixer (480d), a fifth frequency mixer (480e), and a sixth frequency mixer (480f), a fourth amplifier (484d), a fifth amplifier (484e), a sixth amplifier (484f), a seventh amplifier (484g), and an eighth amplifier (484h), a quadrature coupler (e.g., a branchline coupler) (494), and a power combiner (e.g., a Wilkinson power combiner) (498).

[0096] The I-BB baseband signals (404a) and the Q-BB baseband signals (404b) may be the I and Q components of the baseband signals (404) having client data encoded therein. The I-BB client-side input (400a) may be configured to transmit the I-BB baseband signals (404a) to the sixth amplifier (484f). The Q-BB client-side input (400b) may be configured to transmit the Q-BB baseband signals (404b) to the seventh amplifier (484g).

[0097] The LO input (400c) may be configured to receive carrier signals (488) from an external LO, and the carrier signals (488) have a continuous waveform (e.g., a sine wave waveform) having a predetermined frequency. The LO input (400c) may be further configured to transmit the carrier signals (488) to the Balun (492).

[0098] Balun (492) may be configured to isolate and / or maintain impedance differences between balanced transmission lines and non-balanced transmission lines. Balun (492) may be further configured to transmit carrier signals (488) to a third frequency mixer (480c).

[0099] The third frequency mixer (480c) may be configured to receive carrier signals (488) from Balun (492), multiply the carrier signals (488) (e.g., by a multiple of 4), and transmit the multiplied carrier signals to the fourth amplifier (484d).

[0100] The fourth amplifier (484d) may be configured to receive carrier signals multiplied from the third frequency mixer (480c), adjust the amplitude of the multiplied carrier signals so that the amplified carrier signals can drive the fourth frequency mixer (480d), and transmit the amplified carrier signals to the fourth frequency mixer (480d).

[0101] The fourth frequency mixer (480d) may be configured to receive carrier signals amplified from the fourth amplifier (484d), multiply the amplified carrier signals (e.g., by a multiple of 2), and transmit the remultiplied carrier signals to the fifth amplifier (484e).

[0102] The fifth amplifier (484e) may be configured to receive carrier signals that have been re-multiplied from the fourth frequency mixer (480d), adjust the amplitude of the re-multiplied carrier signals so that the re-amplified carrier signals can drive the orthogonal coupler (494), and transmit the re-amplified carrier signals to the orthogonal coupler (494).

[0103] The sixth amplifier (484f) may be configured to receive I-BB baseband signals (404a) from the I-BB client side input (400a), adjust the amplitude of the I-BB baseband signals (404a) so that the amplified I-BB input signals can drive the fifth frequency mixer (480e), and transmit the amplified I-BB signals to the fifth frequency mixer (480e).

[0104] The seventh amplifier (484g) may be configured to receive Q-BB baseband signals (404b) from the Q-BB client-side input (400b), adjust the amplitude of the Q-BB baseband signals (404b) so that the amplified Q-BB baseband signals (404b) can drive the sixth frequency mixer (480f), and transmit the amplified Q-BB signals to the sixth frequency mixer (480f).

[0105] The orthogonal coupler (494) may be configured to receive re-amplified carrier signals from the fifth amplifier (484e), split the re-amplified carrier signals into first carrier signals and second carrier signals, transmit the first carrier signals to the fifth frequency mixer (480e), and transmit the second carrier signals to the sixth frequency mixer (480f), wherein the first carrier signals and the second carrier signals are out of phase by 90°.

[0106] The fifth frequency mixer (480e) may be configured to receive I-BB signals amplified from the sixth amplifier (484f), receive first carrier signals from the orthogonal combiner (494), upconvert the amplified I-BB signals into first carrier signals to produce I antenna feed signals having the I component of client data encoded therein and also a predetermined frequency of the carrier signals (488), and transmit the I antenna feed signals to the power combiner (498).

[0107] The sixth frequency mixer (480f) may be configured to receive Q-BB signals amplified from the seventh amplifier (484g), receive second carrier signals from the orthogonal combiner (494), upconvert the amplified Q-BB signals into second carrier signals to produce Q antenna feed signals having a Q component of client data encoded therein and a predetermined frequency of the carrier signals (488), and transmit the Q antenna feed signals to the power combiner (498).

[0108] The power combiner (498) may be configured to receive I antenna feed signals from the fifth frequency mixer (480e), receive Q antenna feed signals from the sixth frequency mixer (480f), combine the I antenna feed signals and the Q antenna feed signals to produce antenna feed signals (412), and transmit the antenna feed signals (412) to the RF interface (464). In some implementations, the RF interface (464) may be electrically connected to one of the first antennas (416) and configured to transmit the antenna feed signals (412) to the first antenna (416). However, in other implementations, one of the first antennas (416) may be included instead of the RF interface (464).

[0109] Now, referring to FIG. 5a, a block diagram of an exemplary implementation of the first receiver (216a) (hereinafter, "first receiver (216a)") shown in FIG. 2 is shown. However, it should be understood that the description of any specific receiver among the receivers (216) may be applicable to any receiver among the receivers (216) described herein. A first receiver (216a) (and, accordingly, each receiver (216)) generally comprises one or more second antennas (516) configured to detect radiation signals (420) received from a first hollow waveguide (208a) and generate one or more antenna output signals (512) (hereinafter, "antenna output signals (512)") based on the radiation signals (420), a receiver circuit (508) configured to receive antenna output signals (512) from the second antennas (516) and generate baseband signals (404) based on the antenna output signals (512), and a client-side output (500) configured to receive baseband signals (404) from the receiver circuit (508) and transmit the baseband signals (404) to one or more external components (e.g., a control module (224)).

[0110] In some embodiments, antenna output signals (512) are received from second antennas (516) on one or more transmission lines (not shown) (hereinafter, "transmission lines"), each of which has two or more conductors (not shown) (hereinafter, "conductors"). In some embodiments, the transmission lines have a first transmission loss, and the first hollow waveguide (208a) has a second transmission loss smaller than the first transmission loss. In some embodiments, the second transmission loss is in the range of 0.001 to 20.00 dB / m / Tb / s.

[0111] In some embodiments, as illustrated in FIG. 5a, the second antennas (516), the receiver circuit (508), and the client-side output (500) may each be placed on a substrate (524). However, in other embodiments, one or more of the second antennas (516), the receiver circuit (508), and the client-side output (500) may be placed on a first substrate (not shown), and one or more of the second antennas (516), the receiver circuit (508), and the client-side output (500) may not be placed on the first substrate. For example, one or more of the second antennas (516), the receiver circuit (508), and the client-side output (500) may be placed on a second substrate (not shown). In such embodiments, the first substrate and the second substrate may be arranged in a stacked array.

[0112] In some embodiments, the substrate (524) may have a plurality of layers (not shown). In such embodiments, one or more of the second antennas (516), receiver circuit (508), and client-side output (500) may be placed on a first layer (not shown), and one or more of the second antennas (516), receiver circuit (508), and client-side output (500) may be placed on a second layer (not shown).

[0113] In some embodiments, one or more of the second antennas (516), receiver circuit (508), and client-side output (500) may be integrated within a monolithic semiconductor die (not shown). In some embodiments, one or more of the second antennas (516), receiver circuit (508), and client-side output (500) may be implemented using one or more of CMOS technology, SiGe semiconductor technology, and III-V compound semiconductor technology.

[0114] In some embodiments, the radiated signals (420) include a first complementary radiated signal (not shown) having a first polarization and a second complementary radiated signal (not shown) having a second polarization different from the first polarization. In such embodiments, the second antennas (516) may be configured to generate antenna output signals (512) based on the radiated signals (420) including the first complementary radiated signal and the second complementary radiated signal. The first polarization and the second polarization may be orthogonal to each other.

[0115] In some embodiments, the radiated signals (420) may be formed by a first complementary radiated signal (not shown) having a first polarization and a second complementary radiated signal (not shown) having a second polarization different from the first polarization, interacting in a first hollow waveguide (208a). In such embodiments, the radiated signals (420) may have a third polarization different from the first polarization and the second polarization. In such embodiments, the second antennas (516) may be configured to generate antenna output signals (512) based on the radiated signals (420) formed by the first complementary radiated signal and the second complementary radiated signal.

[0116] Now, referring to FIG. 5b, in some implementations, the client-side output (500) is configured to receive a serial baseband signal (i.e., baseband signals (404)) from a receiver circuit (508). In such implementations, the first receiver (216a) (and thus any of the receivers (216)) may further include a second deserializer (526) configured to receive baseband signals (404) from the client-side output (500), split the serial baseband signal into parallel baseband signals (428), and transmit the parallel baseband signals (428) to one or more external components (e.g., a control module (224)). In some such implementations, splitting the serial baseband signal into parallel baseband signals (428) utilizes at least one of PDM, TDM, and WDM.

[0117] Now, referring to FIG. 5c, in some implementations, the client-side output (500) is configured to receive parallel baseband signals (428) from the receiver circuit (508). In such implementations, the first receiver (216a) (and thus any of the receivers (216)) may further include a second serializer (532) configured to receive the parallel baseband signals (428) from the client-side output (500) and combine the parallel baseband signals (428) into a serial baseband signal (i.e., baseband signals (404)). In some such implementations, combining the parallel baseband signals (428) into the baseband signals (404) utilizes at least one of PDM, TDM, and WDM.

[0118] Now, referring to FIG. 5d, an exemplary implementation of the receiver circuit (508) illustrated in FIG. 5a through 5c is shown. In some embodiments, the receiver circuit (508) comprises one or more LOs (536) (hereinafter "LO (536)") configured to generate one or more reference signals (540) (hereinafter "reference signals (540)") having a baseband frequency lower than the transmission frequency, one or more down-conversion circuits (552) (hereinafter "down-converter (552)") configured to generate one or more modulation signals (548) (hereinafter "modulation signals (548)") by receiving antenna output signals (512) from the second antennas (516) and reference signals (540) from the LO (536) and down-converting the antenna output signals (512) using the reference signals (540) (i.e., by lowering the frequency of the antenna output signals (512) from the transmission frequency to the baseband frequency, and receiving the modulation signals (548) from the down-converter (552) and demodulating the modulation signals (548) to the baseband It includes one or more demodulation circuits (544) (hereinafter referred to as "demodulators (544)") configured to generate signals (404).

[0119] Now, referring to FIG. 5e, in an implementation configured to receive radiation signals (420) formed by a first complementary radiation signal (not shown) having a first polarization and a second complementary radiation signal (not shown) having a second polarization different from the first polarization, which interact in a first hollow waveguide (208a), the receiver circuit (508) may be configured to receive antenna output signals (512) from the second antennas (516). In such an implementation, the demodulator (544) may be configured to receive modulation signals (548) from a down-converter (552) and demodulate the modulation signals (548) to generate parallel baseband signals (428).

[0120] In some embodiments, the receiver circuit (508) may further include a splitter (556) configured to receive antenna output signals (512) from the second antennas (516) and split the antenna output signals (512) into a plurality of parallel antenna output signals (560) (hereinafter, "parallel antenna output signals (560)"). However, in other embodiments, the second antennas (516) may be configured to detect a first complementary radiation signal and a second complementary radiation signal based on radiation signals (420) received from the first hollow waveguide (208a) and to generate antenna output signals (512) based on the first complementary radiation signal and the second complementary radiation signal.

[0121] In some implementations, detecting a first complementary radiation signal and a second complementary radiation signal based on radiation signals (520) received from a first hollow waveguide (208a) utilizes at least one of PDM, TDM, and WDM.

[0122] Now, referring to FIG. 5f, a block diagram of another exemplary implementation of the first receiver (216a) illustrated in FIG. 2 is shown. In the implementation illustrated in FIG. 5f, the first receiver (216a) includes an RF interface (564) configured to receive antenna output signals (512), a receiver circuit (508) configured to generate baseband signals (404) based on the antenna output signals (512), a client-side output (500) configured to transmit the baseband signals (404) to one or more external components (e.g., a control module (224)), and a digital enhancement and control unit (568) configured to provide digital control and / or processing capabilities to one or more of the components of the first receiver (216a).

[0123] In the illustrated embodiment, the receiver circuit (508) comprises one or more demodulation blocks (544a) (hereinafter, "demodulation blocks (544a)"), a frequency synthesizer (572) including a PLL (576) and a first LO (536a), a second LO (536b), a first frequency mixer (580a), a second frequency mixer (580b), a first amplifier (584a), a second amplifier (584b), and a third amplifier (584c).

[0124] The RF interface (564) may be configured to transmit antenna output signals (512) to the first amplifier (584a). In some implementations, the RF interface (564) may be configured to receive antenna output signals (512) from one of the second antennas (516). In other implementations, one of the second antennas (516) may be included instead of the RF interface (564).

[0125] The first amplifier (584a) may be configured to receive antenna output signals (512) from the RF interface (564), adjust the amplitude of the antenna output signals (512) so that the amplified transmission signals can drive the first frequency mixer (580a), and transmit the amplified transmission signals to the first frequency mixer (580a).

[0126] A frequency synthesizer (572) (i.e., the first LO (536a) and PLL (576)) may be configured to generate first carrier signals having a continuous waveform (e.g., a sine wave waveform) having a predetermined frequency (e.g., within the THz frequency band (104), or in some implementations, within the range of 300 GHz to 10 THz). In some implementations, the predetermined frequency of the first carrier signals is in the range of 30 GHz to 300 GHz. In some such implementations, the predetermined frequency of the first carrier signals is 240 GHz. In other implementations, the predetermined frequency of the first carrier signals is in the range of 300 GHz to 3 THz. The first LO (536a) may be further configured to transmit the first carrier signals to a second amplifier (584b).

[0127] The second amplifier (584b) may be configured to receive first carrier signals from the first LO (536a), adjust the amplitude of the first carrier signals to generate amplified carrier signals capable of driving the first frequency mixer (580a), and transmit the amplified carrier signals to the first frequency mixer (580a).

[0128] The first frequency mixer (580a) may be configured to receive antenna output signals (512) from the first amplifier (584a), receive amplified carrier signals from the second amplifier (584b), down-convert the antenna output signals (512) into amplified carrier signals to produce modulation signals having client data encoded therein and also having a BB frequency, and transmit the modulation signals to the third amplifier (584c).

[0129] The third amplifier (584c) may be configured to receive modulation signals from the first frequency mixer (580a), adjust the amplitude of the modulation signals so that the amplified modulation signals can drive the second frequency mixer (580b), and transmit the amplified modulation signals to the second frequency mixer (580b).

[0130] The second LO (536b) may be configured to generate second carrier signals having a continuous waveform (e.g., a sine wave waveform) having a predetermined frequency (i.e., BB frequency). In some implementations, the predetermined frequency (i.e., BB frequency) of the second carrier signals is in the range of 8 GHz to 10 GHz. The second LO (536b) may be further configured to transmit the second carrier signals to a second frequency mixer (580b).

[0131] The second frequency mixer (580b) may be configured to receive modulated signals amplified from the third amplifier (584c), receive second carrier signals from the second LO (536b), down-convert the amplified modulated signals into second carrier signals to produce encoded signals having client data encoded therein and also having a predetermined frequency (i.e., BB frequency) of the second carrier signals, and transmit the encoded signals to the demodulation block (544a).

[0132] The demodulation block (544a) may be configured to receive encoded signals from the second frequency mixer (580b) and to decode the encoded signals into a format suitable for transmission to one or more external components (e.g., control module (224)) to produce baseband signals (404).

[0133] In some implementations, the demodulation block (544a) may include one or more analog-to-digital converters (ADCs), one or more serializers / deserializers (SerDes), one or more rectifier detectors (800) (shown in FIG. 8), and / or circuits operable to decode encoded output signals from modulation formats such as, for example, AM, ASK, PSK, QAM, or QAM16, or variations thereof, to produce baseband signals (404) having client data encoded therein. In some implementations, the demodulation block (544a) may include circuits operable to perform forward error correction (FEC). The demodulation block (544a) may be further configured to transmit the baseband signals (404) to a client-side output (500). In some implementations, the demodulation block (544a) is configured to simply receive encoded signals from the second frequency mixer (580b) and transmit the encoded signals to the client-side output (500) as baseband signals (404).

[0134] In some implementations, the client-side output (500) is a pair of output interfaces. In some such implementations, the client-side output (500) is an LVDS link configured to transmit LVDS signals, and the baseband signals (404) are LVDS signals containing client data encoded therein.

[0135] Now, referring to FIG. 5g, a block diagram of another exemplary implementation of the first receiver (216a) illustrated in FIG. 2 is shown. In the implementation illustrated in FIG. 5g, the first receiver (216a) includes an RF interface (564) configured to receive antenna output signals (512), an LO input (500c) configured to receive carrier signals (588) from an external LO, a receiver circuit (508) configured to generate Q-BB baseband signals (404b) and I-BB baseband signals (404a) based on the antenna output signals (512) and carrier signals (588), and a Q-BB client-side output (500a) and an I-BB client-side output (500b) configured to transmit the Q-BB baseband signals (404b) and I-BB baseband signals (404a), respectively.

[0136] In the illustrated embodiment, the receiver circuit (508a) includes a third frequency mixer (580c), a fourth frequency mixer (580d), a fifth frequency mixer (580e), a sixth frequency mixer (580f), a fourth amplifier (584d), a fifth amplifier (584e), a sixth amplifier (584f), a seventh amplifier (584g), an eighth amplifier (584h), a ninth amplifier (584i), a tenth amplifier (584j), an eleventh amplifier (584k), a twelfth amplifier (584l), a Balun (592), an orthogonal coupler (e.g., a branch line coupler) (594), and a power divider (e.g., a Wilkinson power divider) (598).

[0137] The fourth amplifier (584d) may be configured to receive antenna output signals (512) from the RF interface (564), adjust the amplitude of the antenna output signals (512) so that the amplified transmission signals can drive the power divider (598), and transmit the amplified transmission signals to the power divider (598). In some implementations, the fourth amplifier (584d) is a low-noise amplifier (LNA).

[0138] The power splitter (598) may be configured to receive transmission signals amplified from the fourth amplifier (584d), split the amplified transmission signals into I antenna output signals having an I component of client data encoded therein and Q antenna output signals having a Q component of client data encoded therein, transmit the Q antenna output signals to the third frequency mixer (580c), and transmit the I antenna output signals to the fourth frequency mixer (580d).

[0139] The LO input (500c) may be configured to receive carrier signals (588) from an external LO, and the carrier signals (588) have a continuous waveform (e.g., a sine wave waveform) having a predetermined frequency. The LO input (500c) may be further configured to transmit the carrier signals (588) to the Balun (592).

[0140] Balun (592) may be configured to isolate and / or maintain impedance differences between balanced transmission lines and non-balanced transmission lines. Balun (492) may be further configured to transmit carrier signals (588) to a sixth frequency mixer (580f).

[0141] The sixth frequency mixer (580f) may be configured to receive carrier signals (588) from Balun (592), multiply the carrier signals (588) (e.g., by a multiple of 4), and transmit the multiplied carrier signals to the 12th amplifier (584l).

[0142] The 12th amplifier (584l) may be configured to receive carrier signals multiplied from the 6th frequency mixer (580f), adjust the amplitude of the multiplied carrier signals to generate amplified carrier signals capable of driving the 5th frequency mixer (580e), and transmit the amplified carrier signals to the 5th frequency mixer (580e).

[0143] The fifth frequency mixer (580e) may be configured to receive carrier signals amplified from the 12th amplifier (584l), multiply the amplified carrier signals (e.g., by a multiple of 2), and transmit the re-multiplied carrier signals to the 11th amplifier (584k).

[0144] The 11th amplifier (584k) can be configured to receive carrier signals that have been re-multiplied from the 5th frequency mixer (580e), generate re-amplified carrier signals that can drive the orthogonal coupler (594) by adjusting the amplitude of the re-multiplied carrier signals, and transmit the re-amplified carrier signals to the orthogonal coupler (594).

[0145] The orthogonal coupler (594) may be configured to receive re-amplified carrier signals from the 11th amplifier (584k), split the re-amplified carrier signals into first carrier signals and second carrier signals, transmit the first carrier signals to the 3rd frequency mixer (580c), and transmit the second carrier signals to the 4th frequency mixer (580d), wherein the first carrier signals and the second carrier signals are out of phase by 90°.

[0146] The third frequency mixer (580c) may be configured to receive Q antenna output signals from the power splitter (598), receive first carrier signals from the orthogonal combiner (e.g., branch line combiner) (566), downconvert the Q antenna output signals into the first carrier signals to generate Q-BB intermediate signals having the Q component of the client data encoded therein and also the BB frequency, and transmit the Q-BB intermediate signals to the fifth amplifier (584e).

[0147] The fifth amplifier (584e), the sixth amplifier (584f), and the seventh amplifier (584g) may be configured to receive Q-BB intermediate signals from the third frequency mixer (580c), down-convert the Q-BB intermediate signals to generate Q-BB baseband signals (404b), and transmit the Q-BB baseband signals (404b) to the Q-BB client-side output (500a). In some implementations, the fifth amplifier (584e) is a transimpedance amplifier (TIA), and the sixth amplifier (584f) is a variable-gain amplifier (VGA).

[0148] The fourth frequency mixer (580d) may be configured to receive I antenna output signals from the power splitter (598), receive second carrier signals from the quadrature combiner (594), downconvert the I antenna output signals into second carrier signals to produce I-BB intermediate signals having the I component of client data encoded therein and also the BB frequency, and transmit the I-BB intermediate signals to the eighth amplifier (584h).

[0149] The eighth amplifier (584h), the ninth amplifier (584i), and the tenth amplifier (584j) may be configured to receive I-BB intermediate signals from the fourth frequency mixer (580d), down-convert the I-BB intermediate signals to generate I-BB baseband signals (404a), and transmit the I-BB baseband signals (404a) to the I-BB client-side output (500b). In some implementations, the eighth amplifier (584h) is a TIA, and the ninth amplifier (584i) is a VGA.

[0150] Now, referring to FIG. 6a, a block diagram of an exemplary implementation of the first transceiver (220a) (hereinafter, "first transceiver (220a)") shown in FIG. 2 is illustrated. However, it should be understood that any specific transceiver among the transceivers (220) may be applicable to any transceiver among the transceivers (220) described herein. The first transceiver (220a) (and thus each of the transceivers (220)) generally includes a third transmitter (212c) and a third receiver (216c).

[0151] A third transmitter (212c) is configured to receive one or more first baseband signals (604a) (hereinafter, "first baseband signals (604a)") having first client data encoded therein from one or more external components (e.g., a control module (224)), a client-side input (600a) configured to receive the first baseband signals (604a) from the client-side input (600a) and generate one or more antenna feed signals (612a) (hereinafter, "antenna feed signals (612)") based on the first baseband signals (604a), a transmitter circuit (608a) configured to receive the antenna feed signals (612a) from the transmitter circuit (608a) and generate one or more first radiation signals (420a) (hereinafter, "first radiation signals (420a)") based on the antenna feed signals (612a) and the first radiation It includes one or more first antennas (616a) (hereinafter, "first antennas (616)") configured to couple signals (420a) to a fourth hollow waveguide (208d).

[0152] A third receiver (216c) generally comprises one or more second antennas (616b) (hereinafter "antennas (616b)") configured to detect one or more second radiation signals (620b) (hereinafter "second radiation signals (620b)") received from a third hollow waveguide (208c) and generate one or more antenna output signals (612b) (hereinafter "antenna output signals (612b)") based on the second radiation signals (620b); a receiver circuit (608b) configured to receive antenna output signals (612b) from the second antennas (616b) and generate second baseband signals (604b) based on the antenna output signals (612b); and one or more external components (e.g., control) that receive the second baseband signals (604b) from the receiver circuit (608b) and generate the second baseband signals (604b). It includes a client-side output (600b) configured to be transmitted to the module (224)).

[0153] Each of the components of the first transceiver (220a) (and thus each of the transceivers (220)) may be identical or similar to one or more of the components of the first transmitter (212a) and the first receiver (216a) as described in this specification.

[0154] Now, referring to FIG. 6b, a block diagram of another exemplary implementation of the first transceiver (220a) shown in FIG. 2 is shown. In the implementation illustrated in FIG. 6b, the first transceiver (220a) comprises a client-side input (600a) configured to receive first baseband signals (604a) from one or more external components (e.g., a control module (224)), a transmitter circuit (608a) configured to generate antenna feed signals (612a) based on input signals (640a), a first RF interface (664a) configured to transmit antenna feed signals (612a), a second RF interface (664b) configured to receive antenna output signals (612b), a receiver circuit (608b) configured to generate second baseband signals (604b) based on antenna output signals (612b), a client-side output (600b) configured to transmit second baseband signals (604b) to one or more external components, and digital control for one or more of the components of the first transceiver (220a). It includes a digital enhancement and control unit (668) configured to provide and / or processing capabilities.

[0155] In some implementations, the first transceiver (220a) includes a first RF interface (664a) but lacks a second RF interface (664b). In such implementations, the first RF interface (664a) may be configured to transmit antenna feed signals (612a) and receive antenna output signals (612b). In some implementations, the first transceiver (220a) may have a number of RF interfaces greater than two.

[0156] In the illustrated embodiment, the transmitter circuit (608a) comprises a frequency synthesizer (672) including a PLL (676), a first LO (636a), and a signal distribution block (e.g., a splitter) (698), one or more modulation blocks (644a) (hereinafter referred to as "modulation blocks (644a)"), a second LO (636b), a first frequency mixer (680a), a third frequency mixer (680c), a first amplifier (684a), a third amplifier (684c), and a fifth amplifier (684e).

[0157] In the illustrated implementation, the receiver circuit (608b) includes a frequency synthesizer (672) comprising a PLL (676), a first LO (636a), and a signal distributor (698), a modulation block (644a), a third LO (636c), a second frequency mixer (680b), a fourth frequency mixer (680d), a second amplifier (684b), a fourth amplifier (684d), and a sixth amplifier (684f).

[0158] In some implementations illustrated in FIG. 6b, each of the components of the first transceiver (220a) is placed on a single substrate (624) which may be a part of a semiconductor wafer.

[0159] The modulation block (644a) may be configured to: (1) receive first baseband signals (604a) from a client-side input (600a), encode the first baseband signals (604a) into a format suitable for modulation onto a carrier signal, and transmit the encoded input signals to a third frequency mixer (680c); and (2) receive encoded output signals from a fourth frequency mixer (680d), decode the encoded output signals into a format suitable for transmission to one or more external components (e.g., a control module (224)), and transmit second baseband signals (604b) to a client-side output (600b).

[0160] In some implementations, the modulation block (644a) may include one or more DACs, one or more ADCs, one or more serializers / deserializers (SerDes), one or more folded modulators (700) (illustrated in FIG. 7), one or more rectifier detectors (800) (illustrated in FIG. 8), and / or circuits operable to encode first baseband signals (604a) into a modulation format such as, for example, AM, ASK, PSK, QAM, or QAM16, or variations thereof, and to decode the encoded output signals from the modulation format to produce second baseband signals (604b) having client data encoded therein. In some implementations, the modulation block (644a) may include circuits operable to perform forward error correction (FEC).

[0161] The frequency synthesizer (672) may be configured to generate first carrier signals having a continuous waveform (e.g., a sine wave waveform) having a predetermined frequency (e.g., a THz frequency band (104) or, in some embodiments, a range of 300 GHz to 10 THz). In some embodiments, the predetermined frequency of the first carrier signals is in the range of 30 GHz to 300 GHz. In some such embodiments, the predetermined frequency of the first carrier signals is 240 GHz. In other embodiments, the predetermined frequency of the first carrier signals is in the range of 300 GHz to 3 THz. The frequency synthesizer (672) may be further configured to transmit the first carrier signals to a signal distribution block (698).

[0162] The signal distribution block (698) may be configured to receive first carrier signals from the first LO (636a) and distribute the first carrier signals to the third amplifier (684c) and the fourth amplifier (684d).

[0163] Now, referring to the transmitter circuit (608a), in some implementations, the client-side input (600a) is a pair of input interfaces. In some such implementations, the client-side input (600a) is an LVDS link configured to receive LVDS signals, and the first baseband signals (604a) are LVDS signals containing client data encoded therein. The client-side input (600a) may be further configured to transmit the first baseband signals (604a) to the modulation block (644a).

[0164] The second LO (636b) may be configured to generate second carrier signals having a continuous waveform (e.g., a sine wave waveform) having a predetermined frequency (i.e., BB frequency). In some implementations, the predetermined frequency (i.e., BB frequency) of the second carrier signals is in the range of 8 GHz to 10 GHz. The second LO (636b) may be further configured to transmit the second carrier signals to a third frequency mixer (680c).

[0165] The third frequency mixer (680c) may be configured to receive encoded input signals from the modulation block (644a), receive second carrier signals from the second LO (636b), upconvert the encoded input signals into second carrier signals to produce first modulation signals having client data encoded therein and also having a predetermined frequency (i.e., BB frequency) of the second carrier signals, and transmit the first modulation signals to the fifth amplifier (684e).

[0166] The fifth amplifier (684e) may be configured to receive first modulation signals from the third frequency mixer (680c), adjust the amplitude of the first modulation signals so that the amplified first modulation signals can drive the first frequency mixer (680a), and transmit the amplified first modulation signals to the first frequency mixer (680a).

[0167] The third amplifier (684c) may be configured to receive first carrier signals from the signal distribution block (698), adjust the amplitude of the first carrier signals to generate amplified carrier signals capable of driving the first frequency mixer (680a), and transmit the amplified carrier signals to the first frequency mixer (680a).

[0168] The first frequency mixer (680a) may be configured to receive carrier signals amplified from the third amplifier (684c), receive first modulation signals amplified from the fifth amplifier (684e), upconvert the amplified first modulation signals into amplified carrier signals to produce second modulation signals having a predetermined frequency of the amplified carrier signals (i.e., in the THz frequency band (104), or in some implementations, in the range of 300 GHz to 10 THz) having data encoded therein, and transmit the second modulation signals to the first amplifier (684a).

[0169] The first amplifier (684a) receives second modulation signals from the first frequency mixer (680a), adjusts the amplitude of the second modulation signals so that the amplified second modulation signals can be transmitted by the first RF interface (664a), and can be configured to transmit the amplified second modulation signals to the first RF interface (664a).

[0170] The first RF interface (664a) may be configured to receive second modulation signals amplified from the first amplifier (684a) and to transmit the amplified second modulation signals as antenna feed signals (612a) (i.e., having data encoded therein) having a frequency within a predetermined frequency range (e.g., the THz frequency band (104), or, in some implementations, a range from 300 GHz to 10 THz). In some implementations, the first RF interface (664a) may be connected to one of the antennas (616) and configured to transmit the antenna feed signals (612a) to the antenna (616). However, in other implementations, one of the antennas (616) may be included instead of the first RF interface (664a).

[0171] Now, referring to the receiver circuit (608b), the second RF interface (664b) may be configured to receive antenna output signals (612b) (i.e., having client data encoded therein) in a predetermined frequency range (e.g., within the THz frequency band (104), or in some implementations, within the range of 300 GHz to 10 THz) and to transmit the antenna output signals (612b) to the second amplifier (684b). As described in more detail below, the second RF interface (664b) may be configured to receive antenna output signals (612b) from one of the antennas (616). However, in other implementations, one of the antennas (616) may be included instead of the second RF interface (664b).

[0172] The second amplifier (684b) may be configured to receive antenna output signals (612b) from the second RF interface (664b), adjust the amplitude of the antenna output signals (612b) to generate amplified second transmission signals capable of driving the second frequency mixer (680b), and transmit the amplified second transmission signals to the second frequency mixer (680b).

[0173] The fourth amplifier (684d) may be configured to receive first carrier signals from the signal distribution block (698), adjust the amplitude of the first carrier signals to generate amplified carrier signals capable of driving the second frequency mixer (680b), and transmit the amplified carrier signals to the second frequency mixer (680b).

[0174] The second frequency mixer (680b) may be configured to receive second transmission signals amplified from the second amplifier (684b), receive carrier signals amplified from the fourth amplifier (684d), down-convert the amplified second transmission signals into amplified carrier signals to produce third modulation signals having data encoded therein and also having an IF or BB frequency, and transmit the third modulation signals to the sixth amplifier (684f).

[0175] The sixth amplifier (684f) may be configured to receive third modulation signals from the second frequency mixer (680b), adjust the amplitude of the third modulation signals so that the amplified third modulation signals can drive the fourth frequency mixer (680d), and transmit the amplified third modulation signals to the fourth frequency mixer (680d).

[0176] The third LO (636c) may be configured to generate reference signals having a continuous waveform (e.g., a sine wave waveform) having a predetermined frequency (i.e., BB frequency). In some implementations, the predetermined frequency (i.e., BB frequency) of the reference signals is in the range of 8 GHz to 10 GHz. The third LO (636c) may be further configured to transmit the reference signals to the fourth frequency mixer (680d).

[0177] The fourth frequency mixer (680d) may be configured to receive third modulation signals amplified from the sixth amplifier (684f), receive reference signals from the third LO (636c), down-convert the amplified third modulation signals to reference signals to produce encoded output signals having client data encoded therein and also having a predetermined frequency of the reference signals (i.e., BB frequency), and transmit the encoded output signals to the modulation block (644a).

[0178] The client-side output (600b) may be configured to transmit second baseband signals (604b) containing client data encoded therein to one or more external components (e.g., a control module (224)). In some implementations, the client-side output (600b) is a pair of output interfaces. In some such implementations, the client-side output (600b) is an LVDS link configured to transmit LVDS signals, and the second baseband signals (604b) are LVDS signals containing client data encoded therein.

[0179] Now, referring to FIG. 7, a schematic diagram of an exemplary implementation of a folded modulator (700) configured according to the present disclosure is shown. The folded modulator (700) may be configured to perform broadband direct modulation to generate encoded signals and to do so with minimal distortion. The folded modulator (700) may adopt a cascade architecture (e.g., a “stacked” or “folded” cascade circuit drive) to produce a linear or approximate linearly modulated output (i.e., encoded signals). In implementations where the folded modulator (700) adopts a cascade architecture, the size of the stack may be directly proportional to the bandwidth.

[0180] Now, referring to FIG. 8, a schematic diagram of an exemplary implementation of a rectifier detector (800) configured according to the present disclosure is shown. The rectifier detector (800) may be configured to perform direct detection of input signals (i.e., encoded signals). The rectifier detector (800) may be further configured to generate output signals by detecting the envelope of the encoded signals or one or more amplitude shifts of the encoded signals.

[0181] Now, referring to FIG. 9a, a side view of an exemplary embodiment of an antenna (900) coupled with a fifth hollow waveguide (208e) configured according to the present disclosure is shown. However, it should be understood that any description referring to any specific antenna among the antennas (416, 516, 616, 900) may refer to any antenna among the antennas (416, 516, 616, 900) described herein. As shown in FIG. 8a, the antenna (900) generally comprises a ground plane (904), a radiator (908) mounted on the ground plane (904), and a coaxial feedline (912) electrically connected to the radiator (908). In some embodiments, the antenna (900) may not have a ground plane (904). In some embodiments, the antenna (900) further includes a casing (not shown) that encloses the radiator (908). The antenna (900) may be a vertical antenna (i.e., an antenna extending orthogonally from the substrate) or a horizontal antenna (i.e., an antenna extending laterally from the substrate).

[0182] The radiator (908) may be configured to transmit and detect radiated signals configured for coherent detection. In the illustrated embodiment, the radiator (908) is a helical radiator configured to transmit and detect radiated signals having circular polarization. In this embodiment, the radiator (908) is of length , diameter , and the gap between adjacent turns of the radiator (908). It has. The radiator (908) is preferably at a distance from the fifth hollow waveguide (208e). It is placed in.

[0183] The radiator (908) can be wound in a predetermined direction, such as clockwise (i.e., left-handed winding) or counterclockwise (i.e., right-handed winding). Although the radiator (908) of the antenna (900) is depicted in FIG. 9a as having a right-handed winding or counterclockwise rotation direction, it should be understood that the radiator (908) of the antenna (900) may be provided with a left-handed winding or clockwise rotation direction.

[0184] In some implementations, transmission signals may be transmitted to the antenna (900) via a coaxial feed line (912). In other implementations, received RF signals may be transmitted from the antenna (900) via a coaxial feed line (912).

[0185] In some implementations, the length of the radiator (908) may be proportional to the wavelength of the signals being transmitted and / or received. In some implementations, the length of the radiator (908) is in the range of 10 micrometers to 10 mm. In some embodiments, the diameter of the radiator (908) may be proportional to the wavelength of the signals being transmitted and / or received. In some embodiments, the diameter of the radiator (908) It is in the range of 10 micrometers to 10 mm. In some embodiments, the spacing between adjacent turns of the radiator (908) It may be in the range of 1 micrometer to 1 mm.

[0186] A predetermined distance at which the antenna (900) is separated from the hollow waveguide (208) It may vary depending on the carrier frequency of the RF signal being transmitted by the antenna (900). In some implementations, a predetermined distance at which the antenna (900) is separated from the hollow waveguide (208). It is in the range of 3 μm to 3 mm. In one embodiment, a predetermined distance at which the antenna (900) is spaced from the hollow waveguide (208). is 1 mm. In some implementations, the antenna (900) can be directly connected to the fifth hollow waveguide (208e).

[0187] Now, referring to FIG. 9b, a top plan view of another exemplary embodiment of an antenna (900) combined with a fifth hollow waveguide (208e) configured according to the present disclosure is shown. The antenna (900) is similar in configuration and function to the antenna (900), except that the antenna (900) comprises a first radiator (908a) formed of a conductive material having a plurality of coplanar windings. In one embodiment, the first radiator (908a) has a spiral shape. The first radiator (908a) may be wound in a predetermined direction, such as clockwise (i.e. left-hand winding) or counterclockwise (i.e. right-hand winding). Although the first radiator (908a) of the antenna (900) is depicted in FIG. 9b as having a right-handed or counterclockwise rotation direction, it should be understood that the first radiator (908a) of the antenna (900) may be provided with a left-handed or clockwise rotation direction.

[0188] Other implementations of the antenna (900) include a gain horn antenna, a Cassegrain antenna, an omnidirectional antenna, a horn lens antenna, a spot focus antenna, a waveguide probe antenna, a scalar feed horn antenna, a wide-angle scalar feed horn antenna, a trihedral antenna, and a conical horn antenna.

[0189] Now, referring to FIG. 10, another exemplary embodiment of the antenna (900) is illustrated herein. As illustrated in FIG. 10, the antenna (900) may be implemented as a bifilar helix antenna. The bifilar helix antenna (900) generally comprises a ground plane (904a) having a first differential pad (1100a) and a second differential pad (1100b), and a second radiator (908b) mounted on the ground plane (904a). In some embodiments, the bifilar helix antenna (900) may not have a ground plane (904a). The second radiator (908b) generally has a double helix shape and may have a first feed point (1104a) electrically connected to the first differential pad (1100a) and a second feed point (1104b) electrically connected to the second differential pad (1100b). The first coaxial feed line (1108a) and the second coaxial feed line (1108b) may each be electrically connected to the first differential pad (1100a) and the second differential pad (1100b), respectively.

[0190] In some implementations, the second radiator (908b) may be configured to transmit and detect differential radiation signals. That is, in the transmitting direction, the second radiator (908b) may receive a first complementary antenna feed signal from the first feed point (1104a), receive a second complementary antenna feed signal from the second feed point (1104b), and transmit radiation signals based on the first complementary antenna feed signal and the second complementary antenna feed signal. Also, in the receiving direction, the second radiator (908b) may receive radiation signals and provide a first complementary antenna output signal to the first feed point (1104a) and a second complementary antenna output signal to the second feed point (1104b). In such implementations, the first complementary antenna output signal and the second complementary antenna output signal may have the same magnitude but opposite phases (i.e., phases out by 180°).

[0191] The second radiator (908b) may be wound in a predetermined direction, such as clockwise or counterclockwise. Although the second radiator (908b) of the bipilar helix antenna (900) is depicted in FIG. 9 as having a left-handed winding or clockwise rotation direction, it should be understood that the second radiator (908b) of the bipilar helix antenna (900) may be provided with a right-handed winding or counterclockwise rotation direction.

[0192] The second radiator (908b) may include a first radiator portion (1112) and a second radiator portion (1114). The first radiator portion (1112) has a first end formed by a first feed point (1104a) and a second end (1116) spaced apart from the first feed point (1104a) by a predetermined distance. The first radiator portion (1112) has a spiral (i.e., helix shape) shape. The second radiator portion (1114) has a third end formed by a second feed point (1104b) and a fourth end (1118) spaced apart from the second feed point (1104b) by a predetermined distance. The second radiator portion (1114) has a spiral (i.e., helix shape) shape. The second end (1116) of the first radiator part (1112) is connected to the fourth end (1118) of the second radiator part (1114).

[0193] Now, referring to FIGS. 11 and 12, another exemplary embodiment of the bipilar helix antenna (900) illustrated in FIG. 10 is shown. As illustrated in FIGS. 11 and 12, in some embodiments, a conductive cone (1200) may be provided to surround the bipilar helix antenna (900) (i.e., so that the bipilar helix antenna (900) is surrounded inside the conductive cone (1200). The second radiator (908b) may be wound in a predetermined direction, such as clockwise or counterclockwise. Although the second radiator (908b) of the bipilar helix antenna (900) enclosed within the conductive cone (1200) is depicted in FIG. 11 and FIG. 12 as having a left-handed winding or a clockwise rotation direction, it should be understood that the second radiator (908b) of the bipilar helix antenna (900) enclosed within the conductive cone (1200) may be provided with a right-handed winding or a counterclockwise rotation direction.

[0194] The conductive cone (1200) may have a first end (1204a), a second end (1204b) opposite the first end (1204a), and a side wall (1208) extending between the first end (1204a) and the second end (1204b). The side wall (1208) may define a first opening (1212a) at the first end (1204a) and a second opening (1212b) at the second end (1204b). As illustrated in FIGS. 11 and 12, the first end (1204a) of the conductive cone (1200) generally has a diameter of the second end (1204b) of the conductive cone (1200). Shorter diameter Receives.

[0195] A bipilar helix antenna (900) enclosed within a conductive cone (1200) can be configured to transmit circularly polarized signals having a relatively high gain (e.g., 10 dBi, 12 dBi, 14 dBi, 15 dBi, 16 dBi, 18 dBi, or 20 dBi, a gain exceeding 6 dBi relative to an isotropic antenna). In the embodiments illustrated in FIGS. 11 and 12, the bipilar helix antenna (900) enclosed within a conductive cone (1200) can function as an efficient wide-bandwidth polarizer. That is, the bipilar helix antenna (900) enclosed within the conductive cone (1200) can be configured to transmit circularly polarized RF signals with high radiation efficiency (greater than 50%, such as 60%, 70%, 75%, 80%, 85%, 90%, or 95%). Losses in radiation efficiency are generally attributed to losses in conductors or substrates. Additionally, the bipilar helix antenna (900) enclosed within the conductive cone (1200) can be configured to transmit circularly polarized signals with a wide bandwidth (greater than 10% of the center frequency, such as 12%, 14%, 15%, 16%, 18%, 20%, 22%, 24%, or 25%).

[0196] The diameter of the bipilar helix antenna (900) may be smaller than the wavelength of the signals transmitted by the bipilar helix antenna (900). In some embodiments, the conductive cone (1200) may be made of a conductive material such as aluminum, copper, silver, gold, other conductive metals, combinations thereof, and / or similar.

[0197] It will be understood by those skilled in the art that circularly polarized signals transmitted by the radiator (908) of the first specific antenna among the antennas (900) can be received only by the radiator (908) of the second specific antenna among the antennas (900) having the same rotation direction. That is, for example, the radiator (908) shown in FIG. 8a and the first radiator (908a) shown in FIG. 8b are depicted as having a right-handed or counterclockwise rotation direction. As a result, the circularly polarized RF signals transmitted by the radiator (908) shown in FIG. 9a or the first radiator (908a) shown in FIG. 9b will have right-hand circular polarization (RHCP). On the other hand, the second radiator (908b) shown in FIG. 10 through 12 is depicted as having a left-handed or clockwise rotation direction. As a result, the circularly polarized RF signals transmitted by the second radiator (908b) shown in FIGS. 10 to 12 will have left-hand circular polarization (LHCP).

[0198] Because circularly polarized signals transmitted by the radiator (908) of the first specific antenna among the antennas (900) can only be received by the radiator (908) of the second specific antenna among the antennas (900) having the same rotation direction, circularly polarized RF signals (i.e., RHCP RF signals) transmitted by the first radiator (908a) depicted in FIG. 9a or the radiator (908a) depicted in FIG. 9b cannot be received by the second radiator (908b) depicted in FIG. 10 to 12. Similarly, circularly polarized signals (i.e., LHCP RF signals) transmitted by the second radiator (908b) depicted in FIG. 10 to 12 cannot be received by the radiator (908) depicted in FIG. 9a or the first radiator (908a) depicted in FIG. 9b. However, circularly polarized signals (i.e., RHCP RF signals) transmitted by the radiator (908) depicted in FIG. 8a can be received by the first radiator (908a) depicted in FIG. 9b, and circularly polarized signals (i.e., LHCP RF signals) transmitted by the second radiator (908b) depicted in FIG. 10 can be received by the second radiator (908b) depicted in FIG. 11 and FIG. 12.

[0199] Now, referring to FIG. 13, an illustration of an electric field (1300) produced by a bipilar helix antenna (900) enclosed within a conductive cone (1200) illustrated in FIG. 11 and FIG. 12 is shown. As illustrated in FIG. 13, the bipilar helix antenna (900) enclosed within a conductive cone (1200) may be operable to produce an electric field (1300) such that the near-field region of the electric field (1300) and the far-field region of the electric field (1300) are established with greater directivity than that provided by conventional antennas. Additionally, the bipilar helix antenna (900) enclosed within a conductive cone (1200) may be operable to produce an electric field (1300) in a manner that does not interfere with the circular polarization of circularly polarized radiation signals transmitted by the second radiator (908b).

[0200] Now, referring to FIG. 14, a diagram of the radiation pattern (1400) of a bipilar helix antenna (900) enclosed within the conductive cone (1200) shown in FIG. 11 and FIG. 12 is illustrated. The radiation pattern (1400) can correspond to a transmission signal having a frequency of 2,000 GHz and a phase of 0°. As shown in FIG. 14, the first curve (1404) shows the LHCP gain of the bipilar helix antenna (900) enclosed within the conductive cone (1200), while the second curve (1408) shows the total directivity of the bipilar helix antenna (900) enclosed within the conductive cone (1200). The difference between the first curve (1404) and the second curve (1408) may represent metal loss and polarization loss. As illustrated in FIG. 14 and as previously described in relation to FIG. 13, a bipilar helix antenna (900) enclosed within a conductive cone (1200) can be operated to produce an electric field (1300) such that the near-field region (1304) and the far-field region (1308) of the electric field (1300) are established with greater directivity than that provided by conventional antennas.

[0201] Now, referring to FIGS. 15 and 16, side views of exemplary embodiments of a non-uniform bipilar helix antenna (1500) (hereinafter referred to as "non-uniform antenna (1500)") configured according to the present disclosure are shown. Since the size of the helix determines the operating frequency, it is effective to provide an antenna having a non-uniform design. By varying the characteristic dimensions of the helix, a wider band of frequencies can be effectively radiated.

[0202] Similar to the bipilar helix antenna (900) described above, the non-uniform antenna (1500) may include a ground plane (904a) having a first differential pad (1100a) and a second differential pad (1100b), and a non-uniform third radiator (908c) mounted on the ground plane (904a). The third radiator (908c) may have a plurality of turns (1504a-n) including at least a first turn (1504a) and a second turn (1504b). For clarity, only the first turn (1504a) and the second turn (1504b) are indicated by reference letters. The first turn (1504a) may have a first characteristic dimension, while the second turn (1504b) may have a second characteristic dimension different from the first characteristic dimension. The first turn (1504a) may be adjacent to the second turn (1504b) or may not be adjacent to the second turn (1504b) (i.e., may be spaced apart from it).

[0203] In the implementation illustrated in FIG. 15, the first turn (1504a) is the first pitch With, the second turn (1504b) is the second pitch With, the first pitch Silver is the second pitch It is smaller than. In the implementation illustrated in FIG. 16, the first turn (1504a) is the first pitch With, the second turn (1504b) is the second pitch With, the first pitch Silver is the second pitch It is bigger than

[0204] In some implementations, the non-uniform antenna (1500) may not have a ground plane (904a). The third radiator (908c) generally has a double helix shape and may have a first feed point (1104a) electrically connected to the first differential pad (1100a) and a second feed point (1104b) electrically connected to the second differential pad (1100b). The first coaxial feed line (1108a) and the second coaxial feed line (1108b) may each be electrically connected to the first differential pad (1100a) and the second differential pad (1100b), respectively.

[0205] In some implementations, the third radiator (908c) may be configured to emit and receive differential signals. That is, in the transmitting direction, the third radiator (908c) may receive a first complementary signal from the first feed point (1104a), a second complementary signal from the second feed point (1104b), and transmit a transmission signal. Also, in the receiving direction, the third radiator (908c) may receive the transmission signal and provide the first complementary signal to the first feed point (1104a) and provide the second complementary signal to the second feed point (1104b). In such implementations, the first complementary signal and the second complementary signal may have the same magnitude but opposite phases (i.e., out of phase by 180°).

[0206] The third radiator (908c) may be wound in a predetermined direction, such as clockwise or counterclockwise. Although the third radiator (908c) of the non-uniform antenna (1500) is depicted in FIGS. 15 and 16 as having a right-handed winding or a counterclockwise rotation direction, it should be understood that the third radiator (908c) of the non-uniform antenna (1500) may be provided with a left-handed winding or a clockwise rotation direction.

[0207] The third radiator (908c) may include a first radiator portion (1112) and a second radiator portion (1114). The first radiator portion (1112) has a first end formed by a first feed point (1104a) and a second end (1116) spaced apart from the first feed point (1104a) by a predetermined distance. The first radiator portion (1112) has a spiral (i.e., helix shape) shape. The second radiator portion (1114) has a third end formed by a second feed point (1104b) and a fourth end (1118) spaced apart from the second feed point (1104b) by a predetermined distance. The second radiator portion (1114) has a spiral (i.e., helix shape) shape. Although the second end (1116) and the fourth end (1118) are shown as being separated from each other, it should be understood that in some embodiments, the second end (1116) of the first radiator part (1112) is connected to the fourth end (1118) of the second radiator part (1114).

[0208] The non-uniform antenna (1500) provides a wider frequency response compared to the uniform antennas existing in the prior art and the uniform bipilar helix antennas discussed herein. While the mathematical formula for the helical shape of the non-uniform radiator (908c) of the non-uniform antenna (1500) in three-dimensional space is shown in Table 1 below and the graph (1700) shown in FIG. 17, the polarization distinguishing characteristics of the uniform antenna over a frequency range of 0.80 THz to 1.40 THz are shown in the graph (1800) shown in FIG. 18. As shown in FIG. 17 and FIG. 18, the polarization distinguishing characteristics can be determined by subtracting the left-hand circular polarization directivity (i.e., DirLHCP) from the right-hand circular polarization directivity (i.e., DirRHCP). As shown in Table 1 and FIG. 16, the right-hand circular polarization directivity (i.e., DirRHCP) of the non-uniform antenna (1500) can be relatively constant in the frequency range of 0.80 THz to 1.40 THz (i.e., 11.5 dBi ± 1 dBi). Furthermore, as shown in FIG. 17, the polarization distinction characteristic (i.e., DirRHCP - DirLHCP) of the non-uniform antenna (1500) is maintained above 25 dB over the frequency range of 0.80 THz to 1.40 THz. Conversely, as shown in FIG. 18, the polarization distinction characteristic (i.e., DirRHCP - DirLHCP) of the uniform antenna drops below 25 dB at the edges of the band and is slightly below 25 dB in the mid-band range.

[0209]

[0210] Now, referring to FIGS. 18 and 20, side views of more exemplary embodiments of the non-uniform antenna (1500) illustrated in FIGS. 15 and 16 are shown. For clarity, the differential pads (1100) and feed points (1104) are not indicated by reference letters in FIGS. 18 and 19. In the embodiments illustrated in FIGS. 19 and 20, the first characteristic dimension and the second characteristic dimension are diameters, not pitches. In the embodiment illustrated in FIG. 19, the first turn (1504a) is the first diameter Having, the second turn (1504b) is the second diameter Having, the first diameter Silver second diameter It is smaller than. In the implementation illustrated in FIG. 20, the first turn (1504a) is the first diameter Having, the second turn (1504b) is the second diameter having, the first diameter Silver second diameter It is bigger than

[0211] Pitches of the turns (1504) of the third radiator (908c) Rather than the diameters of the turns (1504) of the third radiator (908c) Changing it can be advantageous for different bands or for different ground plane dimensions, wire dimensions, etc.

[0212] It should be understood that a third radiator (908c) and / or a non-uniform antenna (1500) may be included in place of any of the respective radiators (908) and / or antennas (900) described herein. Additionally, it should be understood that although the second turn (1504b) is depicted as being immediately adjacent to the first turn (1504a), there may be one or more turns between the first turn (1504a) and the second turn (1504b). Finally, it should be understood that although the first turn (1504a) is depicted as being immediately adjacent to the ground plane (904a), there may be one or more turns between the ground plane (904a) and the first turn (1504a).

[0213] Now, referring to FIGS. 21 and FIGS. 22a through 22c, a differential waveguide probe antenna (2100) configured according to the present disclosure is illustrated herein. The differential waveguide probe antenna (2100) is configured to generate and transmit a transmission signal. Conversely, the differential waveguide probe antenna (2100) is further configured to receive a transmission signal. The differential waveguide probe antenna (2100) includes a pair of waveguide probes (2104) comprising a first waveguide probe (2104a) and a second waveguide probe (2104b).

[0214] In some implementations, the differential waveguide probe antenna (2100) may further include an intermediate waveguide (2108) configured to propagate a transmission signal. In such implementations, the differential waveguide probe antenna (2100) may be further configured to generate a transmission signal and transmit it into the intermediate waveguide (2108). Conversely, in such implementations, the differential waveguide probe antenna (2100) may be further configured to receive a transmission signal from the intermediate waveguide (2108).

[0215] The intermediate waveguide (2108) may have a first end (2112a), a second end (2112b) opposite the first end (2112a) (the first end (2112a) and the second end (2112b), collectively, "ends (2112)"), and a surface (2116) extending between the ends (2112). In some embodiments, a rear reflector (2118) may be in contact with the first end (2112a). The surface (2116) may be composed of metal and has a diameter smaller than 2 wavelengths (i.e., 60 μm) of the transmission signal at 10 THz (or the maximum frequency in the frequency band occupied by the transmission network (200)) and larger than 1 / 2 wavelength (i.e., 0.5 mm) at 300 GHz (or the minimum frequency in the frequency band occupied by the transmission network (200)). It may have. The intermediate waveguide (2108) may be configured in this way to ensure that one or more intended waveguide modes are established. That is, if the intermediate waveguide (2108) is configured to a smaller size, one or more intended waveguide modes cannot be propagated, and if the intermediate waveguide (2108) is configured to a larger size, one or more unintended waveguide modes may be excited. In some implementations, one or more intended waveguide modes of the intermediate waveguide (2108) are sufficiently matched with one or more intended waveguide modes of the hollow waveguide (208) so that the coupling loss between the intermediate waveguide (2108) and the hollow waveguide (208) is minimized (e.g., the coupling loss is in the range of 0.1 dB to 5.0 dB).

[0216] Waveguide probes (2104) may be positioned on opposite sides of the surface (2116) of the intermediate waveguide (2108) and may extend into the intermediate waveguide (2108) toward each other, but may be spaced apart from each other by a certain distance. Thus, the waveguide probes (2104) can establish a strong electric field corresponding to one or more intended waveguide modes. Each of the waveguide probes (2104) may be excited by a transmission signal. In some implementations, each of the waveguide probes (2104) may be excited by a transmission signal of the same intensity and / or opposite phase. That is, the waveguide probes (2104) may be configured to receive the transmission signal as a differential signal having a first complementary signal and a second complementary signal, and also to generate and transmit the transmission signal in the form of an electromagnetic wave. Conversely, the waveguide probes (2104) may be further configured to receive a transmission signal and also provide a transmission signal as a differential signal having a first complementary signal and a second complementary signal.

[0217] In some embodiments, the intermediate waveguide (2108) may have a flared end at the second end (2112b) configured to facilitate mode transition between the intermediate waveguide (2108) and the hollow waveguide (208). In such embodiments, the surface (2116) at the flared end is diameter Larger diameter It may have a flared end. In some such embodiments, the flared end may be formed integrally with the intermediate waveguide (2108). However, in other such embodiments, the flared end may be configured as a horn (2120) that is separate from but coupled to the intermediate waveguide (2108). The horn (2120) may have a first end (2124a) in contact with a second end (2112b) of the intermediate waveguide (2108), a second end (2124b) opposite the first end (2124a) (the first end (2124a) and the second end (2124b), collectively "ends (2124)"), and a curved surface (2128) extending between the ends (2124). The curved surface (2128) at the first end (2124a) has a diameter Same diameter as It may have a differential waveguide probe antenna (2100). The differential waveguide probe antenna (2100) may be configured to transmit a transmission signal into a hollow waveguide (208) with a wide bandwidth (i.e., more than 50%), because the energy contribution from each of the waveguide probes (2104) effectively cancels out unintended higher-order waveguide modes of the other waveguide probe (2104), at least partially. The polarization distinction characteristics of the differential waveguide probe antenna (2100) over a frequency range of 0.60 THz to 1.80 THz are shown in the graph (2500) illustrated in FIG. 22d.

[0218] Now, referring to FIGS. 23, 24a, and 24b, an exemplary embodiment of a differential tapered antenna (2600) configured according to the present disclosure is illustrated. The differential tapered antenna (2600) is configured to generate and transmit a transmission signal in the form of an electromagnetic wave—and, conversely, to receive a transmission signal in the form of an electromagnetic wave, and a first conductor (2604a) and a distance from the first conductor (2604a). It includes a pair of conductors including a second conductor (2604b) (collectively, "conductors (2604)") that is spaced apart by that amount.

[0219] The differential tapered antenna (2600) may be similar to a tapered slot antenna in some respects and to a ridged horn antenna in some respects. However, the differential tapered antenna (2600) differs from the aforementioned antennas in that the differential tapered antenna (2600) has a differential launch structure and is coupled into a hollow waveguide (208) so that the transmitted signal has multiple waveguide modes.

[0220] In the embodiments illustrated in FIG. 23, FIG. 24a, and FIG. 24b, the intermediate waveguide (2108) has a first planar and longitudinal curved surface (2608a) and a second planar and longitudinal curved surface (2608b) (collectively “surfaces (2608)”) that delineate the space (2612). In the embodiments illustrated in FIG. 23, FIG. 24a, and FIG. 24b, conductors (2604) collectively define the surfaces (2608) of the intermediate waveguide (2108) and form a space (2612) between the conductors (2604). As described above, the intermediate waveguide (2108) is configured to propagate a transmission signal in the form of an electromagnetic wave. In such implementations, the differential tapered antenna (2600) may be further configured to generate a transmission signal and transmit it into an intermediate waveguide (2108) and also receive a transmission signal from the intermediate waveguide (2108).

[0221] In some implementations, the distance between the first conductor (2604a) and the second conductor (2604b) at the first end (2112a) of the intermediate waveguide (2108) is smaller than 2 wavelengths of the transmitted signal at 10 THz (or the maximum frequency in the frequency band occupied by the transmission network (200)) and larger than 1 / 2 wavelength at 300 GHz (or the minimum frequency in the frequency band occupied by the transmission network (200). distance may be selected to establish a single waveguide mode for the frequency of the transmitted signal. In some implementations, the distance between the conductors (2604) at the second end (2112b) of the intermediate waveguide (2108) is distance It is larger than that. This tapered shape can establish a continuously scaled geometry that enables an ultra-wideband (i.e., greater than 50%) bandwidth. As energy is launched along the conductors (2604), one or more intended waveguide modes are established between the conductors (2604) and subsequently launched into the intermediate waveguide (2108).

[0222] In some embodiments, each of the conductors (2604) may be fed a transmission signal of the same intensity and / or opposite phase. That is, the conductors (2604) may be configured to receive the transmission signal as a differential signal having a first complementary signal and a second complementary signal, and also to generate and transmit the transmission signal in the form of an electromagnetic wave. Conversely, the conductors (2604) may be further configured to receive the transmission signal and provide the transmission signal as a differential signal having a first complementary signal and a second complementary signal.

[0223] The thickness and width of the transmission lines at the feed point may be selected to establish a characteristic impedance that matches the receiver and / or driver. Those skilled in the art will understand how to perform such calculations. As shown in FIG. 24b, the differential tapered antenna (2600) may further include one or more ground connections, such as a first ground connection (2800a) and a second ground connection (2800b). The polarization distinction characteristics of the differential tapered antenna (2600) over a frequency range of 0.50 THz to 2.00 THz are shown in the graph (2900) illustrated in FIG. 24c.

[0224] Now, referring to FIG. 25, an exemplary embodiment of a differential microstrip patch antenna (3000) configured according to the present disclosure is illustrated herein. The differential microstrip patch antenna (3000) is configured to generate and transmit a transmission signal in the form of electromagnetic waves—and, conversely, to receive a transmission signal in the form of electromagnetic waves, and a first microstrip patch antenna (3004a) and a distance from the first microstrip patch antenna (3004a). It includes a pair of microstrip patch antennas, including a second microstrip patch antenna (3004b) (collectively, "microstrip patch antennas (3004)") spaced apart by a certain amount.

[0225] In some embodiments, the differential microstrip patch antenna (3000) may further include a horn (2120) having a first end (2124a) proximal to the microstrip patch antennas (3004), a second end (2124b) distal to the microstrip patch antennas (3004), and a curved surface (2128) extending between the ends (2124). The curved surface (2028) at the first end (2124a) has a diameter It can have, and the curved surface (2028) at the second end (2124b) is a diameter Larger diameter Can have.

[0226] In some implementations, each of the microstrip patch antennas (3004) may be fed a transmission signal of the same intensity and / or opposite phase. That is, the microstrip patch antennas (3004) may be configured to receive the transmission signal as a differential signal having a first complementary signal and a second complementary signal, and to generate and transmit the transmission signal in the form of an electromagnetic wave. Conversely, the microstrip patch antennas (3004) may be further configured to receive the transmission signal and provide the transmission signal as a differential signal having a first complementary signal and a second complementary signal.

[0227] The differential waveguide probe antenna (2100), differential tapered antenna (2600), and differential microstrip patch antenna (3000) are configured to generate a transmission signal in a linear polarization form.

[0228] Now, referring to FIGS. 26 and FIGS. 27a through 27c, an exemplary embodiment of a single-ended waveguide probe antenna (3008) configured according to the present disclosure is illustrated herein. In some embodiments, the single-ended waveguide probe antenna (3008) may not have a second waveguide probe (2104b) and thus includes only a first waveguide probe (2104a). Also, in some embodiments, the surface (2116) of the intermediate waveguide (2108) may define an opening (3012) through which the first waveguide probe (2104a) extends. As referenced above, in some embodiments, the first end (2112a) of the intermediate waveguide (2108) may serve as a back reflector.

[0229] Now, referring to FIGS. 28, FIGS. 29a through 29c, and FIGS. 30a through 30c, exemplary embodiments of a slot antenna (5800) configured according to the present disclosure are illustrated herein. As illustrated in FIGS. 28, FIGS. 29a through 29c, and FIGS. 30a through 30c, the slot antenna (5800) may include a ground plane (904) disposed between an intermediate waveguide (2108) and rear reflectors (2118). In some embodiments, the ground plane (904) may define one or more slots (3016) (e.g., a first slot (3016a) illustrated in FIGS. 28 and FIGS. 29a through 29c and a second slot (3016b) illustrated in FIGS. 30a through 30c) (hereinafter, "slots (3016)").

[0230] Now, referring to FIG. 31, an exemplary embodiment of a transmission network (3100) (hereinafter referred to as "network (3100)") configured according to the present disclosure is illustrated herein. The network (3100) generally comprises a first network element (3102a), a second network element (3102b), and a hollow waveguide (3104) communicably coupled to the first network element (3102a) and the second network element (3102b).

[0231] Although the network (3100) is described in this specification as comprising a first network element (3102a) that transmits signals and a second network element (3102b) that receives such signals, it should be understood that the network (3100) may be bidirectional, that is, the network (3100) may further comprise a second network element (3102b) that transmits signals and a first network element (3102a) that receives such signals. Accordingly, in some such implementations, the hollow waveguide (3104) may be bidirectional (i.e., configured to propagate signals in both directions simultaneously), but in other such implementations, the hollow waveguide (3104) comprises a first hollow waveguide (not shown) configured to propagate signals in a first direction (e.g., from a first network element (3102a) to a second network element (3102b)), and a second hollow waveguide (not shown) configured to propagate signals in a second direction opposite to the first direction (e.g., from a second network element (3102b) to a first network element (3102a)).

[0232] The first network element (3102a) generally includes one or more transmitters (3106) (hereinafter referred to as "transmitter (3106)" or collectively "transmitters (3106)") and a transmitter antenna array (3108). The transmitter (3106) may include a transmitter circuit configured to generate a plurality of channel signals (3112), such as the first channel signal (3112a) and the second channel signal (3112b) shown in FIG. 30. The transmitter antenna array (3108) may include a plurality of transmitter antennas (3116), such as the first transmitter antenna (3116a) and the second transmitter antenna (3116b) shown in FIG. 30.

[0233] The channel signals (3112) may have input data encoded in a modulation format and a carrier frequency within the range of 300 GHz to 10 THz. That is, the first channel signal (3112a) and the second channel signal (3112b) may have first input data encoded in a first modulation format and a first carrier frequency within the range of 300 GHz to 10 THz. The first channel signal (3112a) and the second channel signal (3112b) are the same signals carrying the same data at the same frequency and having the same modulation format, except that the first channel signal (3112a) and the second channel signal (3112b) may be phase-shifted relative to each other to change the polarization angle of the electromagnetic waves generated by the transmitter antenna array (3108) as discussed below. The second channel signal (3112b) may have second input data (e.g., identical to the first input data) encoded in a second modulation format and a second carrier frequency within the range of 300 GHz to 10 THz.

[0234] Each of the modulation formats described herein may be selected from the group consisting of: IM / DD (IM(intensity-modulation) / DD(direct-detection); NRZ (non-return-to-zero modulation); PAMn (pulse-amplitude-modulation-n); IM-PAMn; mQAM (m-quadrature-amplitude-modulation); and SSB (single-sideband modulation). In implementations where one or more of the modulation formats are PAMn or IM-PAMn, n may be a power of 2 (e.g., 2, 4, 8, 16, 32, 64, etc.). Similarly, in implementations where one or more of the modulation formats are mQAM, m may be a power of 2 greater than or equal to 4 (e.g., 4, 8, 16, 32, 64, etc.).

[0235] In some implementations, the first modulation format and the second modulation format are the same modulation format. In some implementations, the first carrier frequency and the second carrier frequency have the same carrier frequency in the range of 300 GHz to 10 THz.

[0236] The first transmitter antenna (3116a) and the second transmitter antenna (3116b) of the transmitter antenna array (3108) may be configured to receive channel signals (3112) and transmit a plurality of wireless signals (3120), such as the first wireless signal (3120a) and the second wireless signal (3120b) shown in FIG. 30. That is, the first transmitter antenna (3116a) may be configured to receive a first channel signal (3112a) having first input data encoded in a first modulation format and a first carrier frequency and to transmit a first wireless signal (3120a) having first input data encoded in a first modulation format and a first carrier frequency, while the second transmitter antenna (3116b) may be configured to receive a second channel signal (3112b) having second input data encoded in a second modulation format and a second carrier frequency and to transmit a second wireless signal (3120b) having second input data encoded in a second modulation format and a second carrier frequency.

[0237] The first transmitter antenna (3116a) may be configured to induce a first circular polarization within the first radio signal (3120a). In some embodiments, the first circular polarization is left-hand circular polarization (LHCP). However, in other embodiments, the first circular polarization may be right-hand circular polarization (RHCP). Similarly, the second transmitter antenna (3116b) may be configured to induce a second circular polarization within the second radio signal (3120b), wherein the second circular polarization is orthogonal to the first circular polarization. Thus, in embodiments where the first circular polarization is LHCP, the second circular polarization is RHCP. However, in embodiments where the first circular polarization is RHCP, the second circular polarization is LHCP.

[0238] The first transmitter antenna (3116a) and the second transmitter antenna (3116b) are positioned adjacent to each other so that the first radio signal (3120a) and the second radio signal (3120b) interact to form a linearly polarized radio signal (3124) having linear polarization. In some embodiments, the linear polarization is horizontal linear polarization (HLP). In other embodiments, the linear polarization is vertical linear polarization (VLP). Those skilled in the art will understand that HLP or VLP may have a polarization angle, but the polarization may not be perfectly horizontal and may not be perfectly vertical.

[0239] As illustrated in the following mathematical formulas 1 and 2, it should be understood that circular polarization generally consists of linear polarizations having a 90° phase shift:

[0240]

[0241]

[0242] Combining two orthogonal circular polarizations results in a first linear polarization—HLP in this example—as illustrated in Equation 3 below:

[0243]

[0244] Due to the law of conservation of energy, the canceled j terms (i.e., and This does not result in energy loss. Forming a linearly polarized radio signal (3124) from multiple circularly polarized radio signals provides high broadband polarization diversity, which appears to be because the polarization non-idealities of each individual antenna are canceled out and disappear during operation.

[0245] In addition, combining two orthogonal circular polarizations after applying a 180° phase shift to one of the circular polarizations—RHCP in this example—results in a second linear polarization orthogonal to the first linear polarization—VLP in this example—as illustrated in Equation 4 below:

[0246]

[0247] However, applying a 180° phase shift to one of the circular polarizations in this way can result in a decrease in the quality of the excited field.

[0248] Alternatively, for example, by physically rotating the first transmitter antenna (3116a) and the second transmitter antenna (3116b) to apply a physical phase shift of 90° to each of the circular polarizations, and then combining the two orthogonal circular polarizations results in a third linear polarization orthogonal to the first linear polarization—in this example, VLP—as illustrated in Equation 5 below:

[0249]

[0250] Ultimately, those skilled in the art will understand that if a phase shift is applied to each of the circular polarizations in the range of 0° to 180°, the polarization may have a polarization angle that is neither perfectly horizontal nor perfectly vertical.

[0251] The second network element (3102b) generally includes a receiver antenna array (3128) and one or more receivers (3132) (hereinafter referred to as "receiver (3132)" or collectively "receivers (3132)"). The receiver antenna array (3128) may include a plurality of receiver antennas (3136), such as the first receiver antenna (3136a) and the second receiver antenna (3136b) shown in FIG. 30. The receiver (3132) may include a receiver circuit configured to extract input data from channel signals (3112). That is, the receiver circuit may be configured to extract first input data from the first channel signal (3112a) and second input data from the second channel signal (3112b), and these data are preferably the same input data as previously discussed.

[0252] The first receiver antenna (3136a) and the second receiver antenna (3136b) of the receiver antenna array (3128) may be configured to receive wireless signals (3120) and generate channel signals (3112). That is, the first receiver antenna (3136a) may be configured to receive a first wireless signal (3120a) having first input data encoded in a first modulation format and a first carrier frequency and to generate a first channel signal (3112a) having first input data encoded in a first modulation format and a first carrier frequency, while the second receiver antenna (3136b) may be configured to receive a second wireless signal (3120b) having second input data encoded in a second modulation format and a second carrier frequency and to generate a second channel signal (3112b) having second input data encoded in a second modulation format and a second carrier frequency.

[0253] The first receiver antenna (3136a) may be configured to receive radio signals having a first circular polarization. Similarly, the second receiver antenna (3136b) may be configured to receive radio signals having a second circular polarization.

[0254] Now, referring to FIG. 32a, an exemplary implementation of the transmitter (3106) illustrated in FIG. 31 is illustrated therein. As described above, the transmitter (3106) may include a transmitter circuit configured to generate channel signals (3112), such as the first channel signal (3112a) and the second channel signal (3112b) illustrated in FIG. 32a. Accordingly, the transmitter (3106) may include a plurality of channel signal generators (3200) configured to generate channel signals (3112), such as a first channel signal generator (3200a) configured to generate the first channel signal (3112a) illustrated in FIG. 32a and a second channel signal generator (3200b) configured to generate the second channel signal (3112b).

[0255] Misalignment of the transmitter antenna array (3108) with the receiver antenna array (3128) greater than a specific amount (e.g., 3.2°) in the intended polarization A reduction in power to the extent of unintended polarization This can cause an increase in power of the amount—where θ is the misalignment angle—and thereby cause a decrease in polarization diversity. To address this challenge, in some implementations, the transmitter (3106) may further include a phase shift circuit (3204) configured to induce a polarization angle of a linearly polarized radio signal (3124) by inducing a relative phase shift of the first channel signal (3112a) with respect to the second channel signal (3112b). As illustrated in FIG. 31, in such implementations, the phase shift circuit (3204) may be further configured to receive a polarization signal (3208) and also induce a phase shift of the first channel signal (3112a) relative to the second channel signal (3112b) based at least partially on the polarization signal (3208). Inducing a phase shift of the first channel signal (3112a) relative to the second channel signal (3112b) based at least partially on the polarization signal (3208) can have the effect of maximizing the received power of the receiver (3132) by aligning the transmitter antenna array (3108) of the first network element (3102a) with the receiver antenna array (3128) of the second network element (3102b).

[0256] Now, referring to FIG. 32b, an exemplary implementation of the receiver (3132) illustrated in FIG. 31 is illustrated therein. As described above, the receiver circuit may be configured to extract first input data from a first channel signal (3112a) and second input data from a second channel signal (3112b). Accordingly, the receiver (3132) may include a plurality of channel signal generators (3212) configured to generate channel signals (3112), such as a first channel signal generator (3212a) configured to generate the first channel signal (3112a) and a second channel signal generator (3212b) configured to generate the second channel signal (3112b), as illustrated in FIG. 32b.

[0257] As explained above, misalignment of the transmitter antenna array (3108) with the receiver antenna array (3128) greater than a specific amount (e.g., 3.2°) results in power at the intended polarization Reduce by that amount and power in unintended bias By increasing it by that amount, a decrease in polarization diversity may occur. To address this challenge, in some implementations, the receiver (3132) may further include a polarization signal generator (3216) configured to generate a polarization signal (3208) based on the polarization angle between the first channel signal (3112a) and the second channel signal (3112b). The polarization signal generator (3216) may include a power measurement circuit for measuring the power of the first channel signal (3112a) and the second channel signal (3112b).

[0258] To correct the polarization angle induced by the phase shift circuit (3204), a series of first channel signals (3112a) and second channel signals (3112b) having phase shifts known to each other may be supplied to the transmitter antenna array (3108) and subsequently received by the receiver antenna array (3128). The first channel signals (3112a) and second channel signals (3112b) are received by the receiver (3132), and power is analyzed, for example, by a polarization signal generator (3216) to generate polarization signals (3208). The polarization signal generator (3216) may include a receiver processor (3220) that executes logic to generate polarization signals (3208) by searching for the strongest signal and using this information regarding the strongest signal, and a receiver communication unit (3224) that transmits the polarization signals (3208) to a phase shift circuit (3204), wherein the phase shift circuit (3204) may include a transmitter communication unit (3228) that receives the polarization signals (3208) from the polarization signal generator (3216). The polarization signals (3208) have a correlation with specific signals among the first channel signals (3112a) and second channel signals (3112b) having known phase shifts, and may serve as an indicator of power received by the receiver (3132). The phase shift circuit (3204) may include a transmitter processor (3232) that executes operable logic to analyze the polarization signal (3208) and select a phase shift for the first channel signal (3112a) and the second channel signal (3112b) to deliver maximum power to the receiver (3132). Subsequently, the phase shift circuit (3204) subsequently applies the selected phase shift to form the first channel signal (3112a) and the second channel signal (3112b). This correction procedure may be achieved on a periodic basis, such as hourly, daily, and / or similarly.

[0259] Now, referring to FIG. 33, an exemplary implementation of the transmitter antenna array (3108) illustrated in FIG. 31 is shown. It should be understood that the receiver antenna array (3128) may be similar in configuration and function to the transmitter antenna array (3108), except that the receiver antennas (3136) of the receiver antenna array (3128) may be wound in the opposite direction to their respective corresponding parts (i.e., transmitter antennas (3116)) of the transmitter antenna array (3108).

[0260] As described above, the transmitter antenna array (3108) may include transmitter antennas (3116), which may include a first transmitter antenna (3116a) and a second transmitter antenna (3116b) as shown in FIG. 33. The transmitter antennas (3116) of the transmitter antenna array (3108) are shown in FIG. 33 as being arranged in a 1x2 grid pattern.

[0261] In some embodiments, the distance d between the first transmitter antenna (3116a) and the second transmitter antenna (3116b) may be equal to 1.5 times the wavelength λ. However, in other embodiments, the distance d between the first transmitter antenna (3116a) and the second transmitter antenna (3116b) may be a number greater or smaller than 1.5 times the wavelength λ. For example, in some embodiments, the distance d between the first transmitter antenna (3116a) and the second transmitter antenna (3116b) may be smaller than the wavelength λ. However, in other embodiments, the distance d between the first transmitter antenna (3116a) and the second transmitter antenna (3116b) may be a multiple of the wavelength λ.

[0262] Now, referring to FIG. 34, another exemplary embodiment of a transmission network (3100a) (hereinafter referred to as "network (3100a)") configured according to the present disclosure is illustrated herein. The network (3100a) generally comprises a third network element (3102c), a fourth network element (3102d), and a hollow waveguide (3104) communicably coupled to the third network element (3102c) and the fourth network element (3102d).

[0263] Unlike the first network element (3102a) shown in FIG. 31, the third network element (3102c) generally includes a plurality of transmitters (3106), such as the first transmitter (3106a) and the second transmitter (3106b) shown in FIG. 34, and a transmitter antenna array (3108a). Similarly, unlike the second network element (3102b) shown in FIG. 31, the fourth network element (3102d) generally includes a receiver antenna array (3128a) and a plurality of receivers (3132), such as the first receiver (3132a) and the second receiver (3132b) shown in FIG. 34.

[0264] The transmitter antenna array (3108a) may be similar to the transmitter antenna array (3108) illustrated in FIG. 31, except that the first transmitter antenna (3116a) and the second transmitter antenna (3116b) form the first transmitter antenna pair, and the transmitter antenna array (3108a) further includes a third transmitter antenna (3116c) and a fourth transmitter antenna (3116d) to form the second transmitter antenna pair. Although the transmitter antenna array (3108a) is described herein as comprising four of the transmitter antennas (3116), it should be understood that the transmitter antenna array (3108a) may comprise more or fewer than four transmitter antennas (3116).

[0265] The first transmitter (3106a) may be similar to the transmitter (3106) shown in FIG. 31, while the second transmitter (3106b) may be similar to the transmitter (3106) shown in FIG. 30, except that the channel signals (3112) transmitted by the second transmitter (3106b) may include a third channel signal (3112c) and a fourth channel signal (3112d).

[0266] As described above, the channel signals (3112) may have input data encoded in a specific modulation format and a specific carrier frequency within the range of 300 GHz to 10 THz. That is, as described above, the first channel signal (3112a) may have first input data encoded in a first modulation format and a first carrier frequency within the range of 300 GHz to 10 THz, and the second channel signal (3112b) may have second input data encoded in a second modulation format and a second carrier frequency within the range of 300 GHz to 10 THz. Similarly, the third channel signal (3112c) may have third input data encoded in a third modulation format and a third carrier frequency in the range of 300 GHz to 10 THz, and the fourth channel signal (3112d) may have fourth input data encoded in a fourth modulation format and a fourth carrier frequency in the range of 300 GHz to 10 THz.

[0267] In some implementations, two or more of the first modulation format, the second modulation format, the third modulation format, and the fourth modulation format are the same modulation format. For example, the first modulation format and the second modulation format may be the same modulation format. Also, the third modulation format and the fourth modulation format may be the same modulation format.

[0268] In some embodiments, two or more of the first carrier frequency, the second carrier frequency, the third carrier frequency, and the fourth carrier frequency are the same carrier frequency in the range of 300 GHz to 10 THz. For example, the first carrier frequency and the second carrier frequency may be the same carrier frequency; and the third carrier frequency and the fourth carrier frequency may be the same carrier frequency. In some embodiments, two or more of the first carrier frequency and the second carrier frequency may be different from the third carrier frequency and the fourth carrier frequency.

[0269] As described above, the transmitter antennas (3116) of the transmitter antenna array (3108a) may be configured to receive channel signals (3112) and also transmit radio signals (3120), such as the first radio signal (3120a) and the second radio signal (3120b) as shown in FIG. 34, as well as the third radio signal (3120c) and the fourth radio signal (3120d). That is, the third transmitter antenna (3116c) may be configured to receive a third channel signal (3112c) having third input data encoded in a third modulation format and a third carrier frequency and to transmit a third wireless signal (3120c) having third input data encoded in a third modulation format and a third carrier frequency, and the fourth transmitter antenna (3116d) may be configured to receive a fourth channel signal (3112d) having fourth input data encoded in a fourth modulation format and a fourth carrier frequency and to transmit a fourth wireless signal (3120d) having fourth input data encoded in a fourth modulation format and a fourth carrier frequency.

[0270] As described above, the first transmitter antenna (3116a) may be configured to induce a first circular polarization within the first radio signal (3120a), and the second transmitter antenna (3116b) may be configured to induce a second circular polarization within the second radio signal (3120b), wherein the second circular polarization is orthogonal to the first circular polarization. Similarly, the third transmitter antenna (3116c) may be configured to induce a third circular polarization within the third radio signal (3120c), and the fourth transmitter antenna (3116d) may be configured to induce a fourth circular polarization within the fourth radio signal (3120d), wherein the fourth circular polarization is orthogonal to the third circular polarization.

[0271] The first radio signal (3120a) and the second radio signal (3120b) may interact to form a first linearly polarized radio signal (3124a) having a first linear polarization. Similarly, the third radio signal (3120c) and the fourth radio signal (3120d) may interact to form a second linearly polarized radio signal (3124b) having a second linear polarization, wherein the second linear polarization is orthogonal to the first linear polarization. The first linearly polarized radio signal (3124a) may be similar to the linearly polarized radio signal (3124) illustrated in FIG. 30. Similarly, the second linearly polarized radio signal (3124b) may be similar to the linearly polarized radio signal (3124) illustrated in FIG. 31.

[0272] In some implementations, the first linearly polarized radio signal (3124a) has a first polarization angle and the second linearly polarized radio signal (3124b) has a second polarization angle, wherein the first polarization angle and the second polarization angle are offset by a number of degrees within the range of 86.8° to 93.2°.

[0273] The receiver antenna array (3128a) may be similar to the receiver antenna array (3128) illustrated in FIG. 31, except that the first receiver antenna (3136a) and the second receiver antenna (3136b) form the first receiver antenna pair, and the receiver antenna array (3128a) further includes a third receiver antenna (3136c) and a fourth receiver antenna (3136d) that form the second receiver antenna pair. Although the receiver antenna array (3128a) is described herein as comprising four of the receiver antennas (3136), it should be understood that the receiver antenna array (3128a) may include an even number of receiver antennas (3136), more or fewer than four.

[0274] While the first receiver (3132a) may be similar to the receiver (3132) shown in FIG. 31, the second receiver (3132b) may be similar to the receiver (3132) shown in FIG. 30, except that the receiving channel signals (3112) by the second receiver (3132b) may include a third channel signal (3112c) and a fourth channel signal (3112d).

[0275] As described above, the receiver antennas (3136) of the receiver antenna array (3128a) may be configured to receive wireless signals (3120) and generate channel signals (3112). That is, the third receiver antenna (3136c) may be configured to receive a third wireless signal (3120c) having third input data encoded in a third modulation format and a third carrier frequency and to generate a third channel signal (3112c) having third input data encoded in a third modulation format and a third carrier frequency, and the fourth receiver antenna (3136d) may be configured to receive a fourth wireless signal (3120d) having fourth input data encoded in a fourth modulation format and a fourth carrier frequency and to generate a fourth channel signal (3112d) having fourth input data encoded in a fourth modulation format and a fourth carrier frequency.

[0276] As described above, the first receiver antenna (3136a) may be configured to receive a first wireless signal (3120a) having first input data encoded in a first modulation format and a first carrier frequency and to generate a first channel signal (3112a) having first input data encoded in a first modulation format and a first carrier frequency, while the second receiver antenna (3136b) may be configured to receive a second wireless signal (3120b) having second input data encoded in a second modulation format and a second carrier frequency and to generate a second channel signal (3112b) having second input data encoded in a second modulation format and a second carrier frequency. Similarly, the third receiver antenna (3136c) may be configured to receive a third wireless signal (3120c) having third input data encoded in a third modulation format and a third carrier frequency and to generate a third channel signal (3112c) having third input data encoded in a third modulation format and a third carrier frequency, while the fourth receiver antenna (3136d) may be configured to receive a fourth wireless signal (3120d) having fourth input data encoded in a fourth modulation format and a fourth carrier frequency and to generate a fourth channel signal (3112d) having fourth input data encoded in a fourth modulation format and a fourth carrier frequency.

[0277] Now, referring to FIG. 35a, an exemplary embodiment of the transmitter antenna array (3108a) illustrated in FIG. 34 is shown. It should be understood that a receiver antenna array (3128a) comprising receiver antennas (3136) wound in the same direction as the transmitter antennas (3116) may be similar to the transmitter antenna array (3108a). In some embodiments, the receiver antennas (3136) of the receiver antenna array (3128a) may be wound in the opposite direction to their respective counterparts (i.e., transmitter antennas (3116)) of the transmitter antenna array (3108a).

[0278] As described above, the transmitter antenna array (3108a) may include transmitter antennas (3116), which may include a first transmitter antenna (3116a), a second transmitter antenna (3116b), a third transmitter antenna (3116c), and a fourth transmitter antenna (3116d) as shown in FIG. 35a. The transmitter antennas (3116) of the transmitter antenna array (3108a) appear to be arranged in an nxm grid pattern in FIG. 35a, where n and m are both equal to 2. It should be understood that although the transmitter antennas (3116) of the transmitter antenna array (3108a) shown in FIG. 35a are arranged in a 2x2 grid pattern, the transmitter antennas (3116) of the transmitter antenna array (3108a) may be arranged in any nxm grid pattern—where n and m are both multiples of 2. In some embodiments, the distance d between each of the transmitter antennas (3116) and the nearest neighbor of such transmitter antennas (3116) may be equal to 1.5λ. However, in other embodiments, the distance d between each of the transmitter antennas (3116) and the nearest neighbor of such transmitter antennas (3116) may be a number greater than or less than 1.5λ.

[0279] Now, referring to FIG. 35b, there is a diagram illustrating another exemplary implementation of the transmitter antenna array (3108a) shown in FIG. 34. However, it should be understood that a receiver antenna array (3128a) comprising receiver antennas (3136) wound in the same direction as the transmitter antennas (3116) may be similar to the transmitter antenna array (3108a). In some implementations, the receiver antennas (3136) of the receiver antenna array (3128a) may be wound in the opposite direction to their respective counterparts (i.e., transmitter antennas (3116)) of the transmitter antenna array (3108a).

[0280] As described above, the transmitter antenna array (3108a) may include transmitter antennas (3116), which may include a first transmitter antenna (3116a), a second transmitter antenna (3116b), a third transmitter antenna (3116c), and a fourth transmitter antenna (3116d) as shown in FIG. 35b. The transmitter antennas (3116) of the transmitter antenna array (3108a) are shown in FIG. 35b as being arranged in a 1 x m grid pattern. It should be understood that while the transmitter antennas (3116) of the transmitter antenna array (3108a) shown in FIG. 35b are arranged in a 1 x 4 grid pattern, the transmitter antennas (3116) of the transmitter antenna array (3108a) may be arranged in any 1 x m grid pattern—where m is a multiple of 4.

[0281] As described above, in some embodiments, the distance d between each of the transmitter antennas (3116) and the nearest neighbor among these transmitter antennas (3116) may be equal to 1.5 times the wavelength λ. However, in other embodiments, the distance d between each of the transmitter antennas (3116) and the nearest neighbor among these transmitter antennas (3116) may be a number greater or smaller than 1.5 times the wavelength λ. For example, in some embodiments, the distance d between each of the transmitter antennas (3116) and the nearest neighbor among these transmitter antennas (3116) may be smaller than the wavelength λ. However, in other embodiments, the distance d between each of the transmitter antennas (3116) and the nearest neighbor among these transmitter antennas (3116) may be a multiple of the wavelength λ.

[0282] Now, referring to FIG. 36, an exemplary implementation of a method (3600) using a network (3100) according to the present disclosure is illustrated herein. As illustrated in FIG. 36, the method (3600) generally comprises: transmitting a first radio signal (3120a) and a second radio signal (3120b) simultaneously from a transmitter antenna array (3108) into a hollow waveguide (3104) – wherein the first radio signal (3120a) and the second radio signal (3120b) have input data (i.e., first input data and second input data) encoded in a modulation format (i.e., respectively a first modulation format and a second modulation format) and also have carrier frequencies within the range of 300 GHz to 10 THz (i.e., respectively a first carrier frequency and a second carrier frequency), and the first radio signal (3120a) has LHCP and the second radio signal (3120b) has RHCP, and the first radio signal (3120a) interacts with the second radio signal (3120b) to form a linearly polarized radio The signal (3124) is formed - (including step (3604)).

[0283] In some embodiments, the method (3600) further comprises, before the transmitting step (step 3604): the step of generating a first radio signal (3120a) by applying a first channel signal (3112a) to a first transmitter antenna (3116a) of a transmitter antenna array (3108); the step of generating a second radio signal (3120b) by applying a second channel signal (3112b) to a second transmitter antenna (3116b) of a transmitter antenna array (3108); and the step of inducing a phase shift of the first channel signal (3112a) in contrast to the second channel signal (3112b) to induce a polarization angle in a linearly polarized radio signal (3124).

[0284] In some such implementations, the method (3600) further comprises the step of receiving a polarization signal (3208), wherein the induction is further defined as inducing a phase shift of the first channel signal (3112a) relative to the second channel signal (3112b) based at least partially on the polarization signal (3208).

[0285] In some implementations, the transmitter antenna array (3108) is the transmitter antenna array (3108a), the input data is the first input data, the modulation format is the first modulation format, the carrier frequency is the first carrier frequency, and the linearly polarized radio signal (3124) is the first linearly polarized radio signal (3124a). In such implementations, the method (3600) may further include the step of simultaneously transmitting a third radio signal (3120c) and a fourth radio signal (3120d) from a transmitter antenna array (3108a) into a hollow waveguide (3104), wherein the third radio signal (3120c) has third input data encoded in a third modulation format and also has a third carrier frequency in the range of 300 GHz to 10 THz, and the fourth radio signal (3120d) has fourth input data encoded in a fourth modulation format and also has a fourth carrier frequency in the range of 300 GHz to 10 THz, and the third radio signal (3120c) has LHCP and the fourth radio signal (3120d) has RHCP, and the third radio signal (3120c) interacts with the fourth radio signal (3120d) to form a second linearly polarized radio signal (3124b).

[0286] In some such implementations, the method (3600) further comprises, before the step of transmitting the third radio signal (3120c): the step of generating the third radio signal (3120c) by applying the third channel signal (3112c) to the third transmitter antenna (3116c) of the transmitter antenna array (3108a); the step of generating the fourth radio signal (3120d) by applying the fourth channel signal (3112d) to the fourth transmitter antenna (3116d) of the transmitter antenna array (3108a); and the step of inducing a phase shift of the third channel signal (3112c) in contrast to the fourth channel signal (3112d) to induce a polarization angle in the second linearly polarized radio signal (3124b).

[0287] In some such implementations, the method (3600) further comprises the step of receiving a polarization signal (3208), wherein the induction is further defined as inducing a phase shift of the third channel signal (3112c) relative to the fourth channel signal (3112d) based at least partially on the polarization signal (3208).

[0288] In some implementations, the first linearly polarized radio signal (3124a) has a first polarization angle, and the second linearly polarized radio signal (3124b) has a second polarization angle, and the first polarization angle and the second polarization angle are offset within the range of 86.8° to 93.2°.

[0289] In some implementations, the transmitting step is further defined as: transmitting a first radio signal (3120a) by a first transmitter antenna (3116a); transmitting a second radio signal (3120b) by a second transmitter antenna (3116b); transmitting a third radio signal (3120c) by a third transmitter antenna (3116c); and transmitting a fourth radio signal (3120d) by a fourth transmitter antenna (3116d), wherein, as shown in FIG. 35a, the first transmitter antenna (3116a), the second transmitter antenna (3116b), the third transmitter antenna (3116c), and the fourth transmitter antenna (3116d) are arranged in an nxm grid pattern, and n and m are at least 2.

[0290] In other embodiments, the transmitting step is further defined as: transmitting a first radio signal (3120a) by a first transmitter antenna (3116a); transmitting a second radio signal (3120b) by a second transmitter antenna (3116b); transmitting a third radio signal (3120c) by a third transmitter antenna (3116c); and transmitting a fourth radio signal (3120d) by a fourth transmitter antenna (3116d), wherein, as illustrated in FIG. 35b, the first transmitter antenna (3116a), the second transmitter antenna (3116b), the third transmitter antenna (3116c), and the fourth transmitter antenna (3116d) are arranged in a 1 x m grid pattern, where m is at least 4.

[0291] Now, referring to FIG. 37a, an exemplary implementation of a dual-polation transmitter network element (3700a) (hereinafter referred to as "transmitter network element (3700a)" configured according to the present disclosure is illustrated herein. As illustrated in FIG. 37a, the transmitter network element (3700a) comprises, for example, a dual-polarized hollow waveguide (3704) configured to simultaneously propagate signals having a first polarization and a second polarization different from the first polarization, exemplarily referred to below as a dual-polarized hollow waveguide, one or more modulators (3708a-n) configured to generate a first channel signal (3712a) and a second channel signal (3712b) (collectively, "channel signals (3712)") (for example, the first modulator (3708a) and the second modulator (3708b) illustrated in FIG. 37a) (collectively, "modulators (3708)"), and a dual-polarized hollow waveguide (3704) that receives the first channel signal (3712a) and the second channel signal (3712b) and also converts the first channel signal (3712a) into the first polarization It may include one or more antennas (3716a-n) (e.g., the first antenna (3716a) and the second antenna (3716b) shown in FIG. 37a) configured to be coupled within and coupled the second channel signal (3712b) to the second polarization within the dual-polarized hollow waveguide (3704) (collectively, "antennas (3716)"). The antennas (3716) may be similar to the antennas (900) described above.

[0292] The channel signals (3712) are also referred to herein as "transmitted channel signals" (3712) (i.e., "first transmitted channel signal (3712a)" and "second transmitted channel signal (3712b)") when viewed from the perspective of the transmitter network element (3700a), and as "received channel signals" (3712) (i.e., "first received channel signal (3712a)" and "second received channel signal (3712b)") when viewed from the perspective of the receiver network element (3700b) (as shown in FIG. 37b). However, it should be understood that while the receiving channel signals (3712) may have the same data and the same RF frequency as the transmitting channel signals (3712), the receiving channel signals (3712) may reveal linear distortions caused by the dual-polarized hollow waveguide (3704) and / or antennas (3716).

[0293] In embodiments where the antennas (3716) include a first antenna (3716a) and a second antenna (3716b), the first antenna (3716a) may be configured to impart a first polarization to the first transmission channel signal (3712a) while coupling the first transmission channel signal (3712a) into a dual-polarized hollow waveguide (3704), and the second antenna (3716b) may be configured to impart a second polarization to the second transmission channel signal (3712b) while coupling the second transmission channel signal (3712b) into a dual-polarized hollow waveguide (3704).

[0294] The first transmission channel signal (3712a) may have first data encoded in a first modulation format, and the second transmission channel signal (3712b) may have second data encoded in a second modulation format. In some implementations, the first modulator (3708a) may be configured to generate the first transmission channel signal (3712a) and the second modulator (3708b) may be configured to generate the second transmission channel signal (3712b), such that the first transmission channel signal (3712a) has a first channel frequency and the second transmission channel signal (3712b) has a second channel frequency, wherein the first channel frequency and the second channel frequency are in the range of 300 GHz to 10 THz. In such implementations, the modulators (3708) may be described as performing "direct modulation". However, in other implementations, the first modulator (3708a) and the second modulator (3708b) each may include an intermediate frequency (IF) modulator configured to generate the first transmission channel signal (3712a) and the second transmission channel signal (3712b) respectively, such that the first transmission channel signal (3712a) has a first intermediate frequency lower than the first channel frequency and the second transmission channel signal (3712b) has a second intermediate frequency lower than the second channel frequency.In such embodiments, each of the first modulator (3708a) and the second modulator (3708b) may further include one or more up-converters (not shown) configured to receive the first transmission channel signal (3712a) and the second transmission channel signal (3712b) respectively, and to up-convert the first transmission channel signal (3712a) and the second transmission channel signal (3712b) such that the first transmission channel signal (3712a) has a first channel frequency and the second transmission channel signal (3712b) has a second channel frequency, wherein the first channel frequency and the second channel frequency are in the range of 300 GHz to 10 THz. In such embodiments, the modulators (3708) may be described as performing "IF modulation".

[0295] The first modulation format and the second modulation format may be selected from the group consisting of: IM / DD (IM(intensity-modulation) / DD(direct-detection); NRZ(non-return-to-zero modulation); PAMn(pulse-amplitude-modulation-n); IM-PAMn; mQAM(m-quadrature-amplitude-modulation); SSB(single-sideband modulation); QPSK(quadrature-phase-shift-keying); and DQPSK (differential-detection QPSK). In some implementations, the first modulation format is identical to the second modulation format. However, in other implementations, the first modulation format is different from the second modulation format. In implementations where one or more of the first modulation format and the second modulation format are PAMn or IM-PAMn, n may be a power of 2 (e.g., 2, 4, 8, 16, 32, 64, etc.). Similarly, the first modulation format and In implementations where one or more of the second modulation formats are mQAM, m can be a power of 2 equal to or greater than 4 (e.g., 4, 8, 16, 32, 64, etc.). It should be understood that 4QAM (i.e., mQAM in implementations where m is equal to 4) can be the same as QPSK.

[0296] In some implementations, the modulators (3708) may be further configured to receive one or more input signals (3720) (e.g., a first input signal (3720a), a second input signal (3720b), a third input signal (3720c), and a fourth input signal (3720d) shown in FIG. 37a (collectively, "input signals (3720)"). In some such implementations, as shown in FIG. 37a, the first input signal (3720a) and the second input signal (3720b) ​​may form a first input signal pair (3724a), and the third input signal (3720c) and the fourth input signal (3720d) may form a second input signal pair (3724b). In such implementations, the first input signal pair (3724a) may have first data encoded in a first modulation format, and the second input signal pair (3724b) may have second data encoded in a second modulation format. Furthermore, in such implementations, the first input signal (3720a) and the third input signal (3720c) may be I input signals, and the second input signal (3720b) ​​and the fourth input signal (3720d) may be Q input signals.

[0297] The first polarization may be orthogonal to the second polarization. In some implementations, the first polarization is left-hand circular polarization (LHCP). In such implementations, the second polarization is right-hand circular polarization (RHCP). In other implementations, the first polarization is horizontal linear polarization (HLP). In such implementations, the second polarization is vertical linear polarization (VLP). Those skilled in the art will understand that HLP and VLP have some rotation so that HLP is not perfectly horizontal and VLP is not perfectly vertical.

[0298] Now, referring to FIG. 37b, there is an illustration of another exemplary implementation of a dual-polarization receiver network element (3700b) (hereinafter, "receiver network element (3700b)") configured according to the present disclosure. As illustrated in FIG. 37b, a receiver network element (3700b) may include a dual-polarized hollow waveguide (3704), antennas (3716) configured to receive a first receiving channel signal (3712a) and a second receiving channel signal (3712b) from the dual-polarized hollow waveguide (3704) (e.g., the first antenna (3716a) and the second antenna (116b) shown in FIG. 37b), and one or more demodulators (3728a-n) configured to receive the first receiving channel signal (3712a) and the second receiving channel signal (3712b) (e.g., the first demodulator (3728a) and the second demodulator (3728b) shown in FIG. 37b) (collectively, "demodulators (3728)").

[0299] In some implementations, the demodulators (3728) may be further configured to produce one or more output signals (3732) (e.g., a first output signal (3732a), a second output signal (3732b), a third output signal (3732c), and a fourth output signal (3732d) (collectively, "output signals (3732)") based on a first receiving channel signal (3712a) and a second output signal (3732b) based on the first receiving channel signal (3712a), and a third output signal (3732c) and a fourth output signal (3732d) based on the second receiving channel signal (3712b)).

[0300] In some implementations, as illustrated in FIG. 37b, the first output signal (3732a) and the second output signal (3732b) may form the first output signal pair (3736a). Similarly, the third output signal (3732c) and the fourth output signal (3732d) may form the second output signal pair (3736b). In such implementations, the first output signal (3732a) and / or the third output signal (3732c) may have phase (I) data, and the second output signal (3732b) and / or the fourth output signal (3732d) may have orthogonal (Q) data. The output signals (3732) may be configured for data detection (i.e., extraction of the first data and the second data).

[0301] In embodiments where the antennas (3716) include a first antenna (3716a) and a second antenna (3716b), the first antenna (3716a) may be configured to receive RF signals having a first polarization, and the second antenna (3716b) may be configured to receive RF signals having a second polarization.

[0302] In some implementations, the first demodulator (3728a) and the second demodulator (3728b) each demodulate the first receiving channel signal (3712a) and the second receiving channel signal (3712b), such that the first output signal (3732a) and the second output signal (3732b) of the first output signal pair (3736a) have a first channel frequency in the range of 300 GHz to 10 THz, and the third output signal (3732c) and the fourth output signal (3732d) of the second output signal pair (3736b) have a second channel frequency in the range of 300 GHz to 10 THz, and based on the first receiving channel signal (3712a), the first output signal pair (3736a) (i.e., the first output signal (3732a) and the second output signal (3732b)) and the second receiving channel It may be configured to produce a second output signal pair (3736b) (i.e., a third output signal (3732c) and a fourth output signal (3732d)) based on the signal (3712b). In such implementations, the demodulators (3728) may be described as performing "direct demodulation". However, in other implementations, the first demodulator (3728a) and the second demodulator (3728b) each may include one or more down-converters (not shown) configured to receive the first receiving channel signal (3712a) and the second receiving channel signal (3712b) respectively, and to down-convert the first receiving channel signal (3712a) and the second receiving channel signal (3712b) such that the first receiving channel signal (3712a) has a first intermediate frequency lower than the first channel frequency and the second receiving channel signal (3712b) has a second intermediate frequency lower than the second channel frequency.In such implementations, each of the first demodulator (3728a) and the second demodulator (3728b) may further include an IF demodulator configured to demodulate the first receiving channel signal (3712a) and the second receiving channel signal (3712b) respectively to produce a first output signal pair (3736a) (i.e., the first output signal (3732a) and the second output signal (3732b)) based on the first receiving channel signal (3712a) and a second output signal pair (3736b) (i.e., the third output signal (3732c) and the fourth output signal (3732d)) based on the second receiving channel signal (3712b). In such implementations, the demodulators (3728) may be described as performing "IF demodulation".

[0303] Now, referring to FIG. 38, a diagram of a dual-polarized signal (3800) comprising a plurality of wavelength-division multiplexed (WDM) signals (3804) according to the present disclosure is shown. The dual-polarized signal (3800) is also referred to herein as a "transmitted dual-pol signal" (3800) in terms of a transmitter network element (3700a) and a "received dual-pol signal" (3800) in terms of a receiver network element (3700b) (shown in FIG. 37b). However, it should be understood that while the received dual-polarized signal (3800) may have the same data and the same frequency as the transmitted dual-polarized signal (3800), the received dual-polarized signal (3800) may reveal linear distortions caused by the dual-polarized hollow waveguide (3704) and / or antennas (3716). Similarly, the WDM signals (3804) are also referred to herein as "transmitted WDM signals" (3804) in terms of the transmitter network element (3700a) and "received WDM signals" (3804) in terms of the receiver network element (3700b) (shown in FIG. 37b). However, it should be understood that while the received WDM signals (3804) may have the same data and the same frequency as the transmitted WDM signals (3804), the received WDM signals (3804) may reveal linear distortions caused by the dual-polarized hollow waveguide (3704) and / or antennas (3716).

[0304] As discussed in more detail below, in some implementations, a transmitter network element (3700a) may be configured to transmit a transmit dual-polarization signal (3800) having a plurality of transmit WDM signals (3804) (e.g., a first transmit WDM signal (3804a) and a second transmit WDM signal (3804b) shown in FIG. 38), wherein each of the transmit WDM signals (3804) comprises a plurality of transmit channel signals (3712), wherein each of the transmit channel signals (3712) has a channel frequency in the range of 300 GHz to 10 THz. The transmitter network element (3700a) may be configured to transmit a plurality of transmit WDM signals (3804) which are at least one (i.e., a single channel with single polarization). Similarly, in some implementations, a receiver network element (3700b) may be configured to receive a received dual-polarization signal (3800) having a plurality of received WDM signals (3804), wherein each of the received WDM signals (3804) includes a plurality of received channel signals (3712), wherein each of the received channel signals (3712) has a channel frequency in the range of 300 GHz to 10 THz.

[0305] The first WDM signal (3804a) is a plurality of first channel signals (3712a) in FIG. 38 (e.g., the first shown in FIG. 38 Channel signal (3712a-1), first Channel signal (3712a-2), first Channel signal (3712a-3), and the first Channel signals (3712a-4)) (collectively "first channel signals (3712a)") are illustrated. Similarly, the second WDM signal (3804b) is a plurality of second channel signals (3712b) in FIG. 38 (e.g., the second shown in FIG. 38). Channel signal (3712b-1), second Channel signal (3712b-2), second Channel signal (3712b-3), and the second Channel signals (3712b-4)) (collectively described as having "second channel signals (3712b)").

[0306] As shown in FIG. 38, the first Channel signal (3712a-1) and second The channel signal (3712b-1) is the first channel frequency It can have, and the first Channel signal (3712a-2) and second The channel signal (3712b-2) is the second channel frequency It can have, and the first Channel signal (3712a-3) and second The channel signal (3712b-3) is the third channel frequency It can have, and the first Channel signal (3712a-4) and second The channel signal (3712b-4) is the fourth channel frequency Each of the WDM signals (3804) may have a predetermined number of channel signals (3712), at least one (i.e., a single channel having a single polarization).

[0307] As illustrated in FIG. 38, in some such implementations, adjacent first channel signals (3712a) may be spaced apart by 200 GHz from each other, and adjacent second channel signals (3712b) may be spaced apart by 200 GHz from each other. However, in other implementations, adjacent first channel signals (3712a) may be spaced apart from each other in the range of 50 GHz to 400 GHz, and adjacent second channel signals (3712b) may be spaced apart from each other in the range of 50 GHz to 400 GHz.

[0308] Now, referring to FIG. 39, an exemplary embodiment of a dual-polarization transmission network (3900) configured according to the present disclosure is illustrated herein. As illustrated in FIG. 39, the dual-polarization transmission network (3900) may include a first dual-polarization network element (3902a), a second dual-polarization network element (3902b), and a dual-polarization hollow waveguide (3704) that extends between the first dual-polarization network element (3902a) and the second dual-polarization network element (3902b) and is configured to simultaneously propagate signals having a first polarization and a second polarization different from the first polarization.

[0309] It should be understood that although the transmission network (3900) is described herein as comprising a first dual-polarization network element (3902a) for transmitting signals and a second dual-polarization network element (3902b) for receiving these signals, the transmission network (3900) may be bidirectional; that is, the transmission network (3900) may further comprise a second dual-polarization network element (3902b) for transmitting signals and a first dual-polarization network element (3902a) for receiving these signals. Accordingly, in some such implementations, the dual-polarization hollow waveguide (3704) may be bidirectional (i.e., configured to propagate signals simultaneously in both directions); However, in other such implementations, the dual-polarization hollow waveguide (3704) comprises a first dual-polarization hollow waveguide (not shown) configured to propagate signals in a first direction (e.g., from a first dual-polarization network element (3902a) to a second dual-polarization network element (3902b)), and a second dual-polarization hollow waveguide (not shown) configured to propagate signals in a second direction opposite to the first direction (e.g., from a second dual-polarization network element (3902b) to a first dual-polarization network element (3902a). Nevertheless, the first dual-polarization network element (3902a) is also referred to herein as "transmitter network element (3902a)", and the second dual-polarization network element (3902b) is also referred to herein as "receiver network element (3902b)".

[0310] The transmitter dual-polarization network element (3902a) comprises a plurality of modulators (3708) (e.g., the first shown in FIG. 39). Modulator (3708a-1), second Modulator (3708b-1), first Modulator (3708a-2), second Modulator (3708b-2), first Modulator (3708a-3), second Modulator (3708b-3), first Modulator (3708a-4), and second It may include a modulator (3708b-4)), a first combiner (3904a), a second combiner (3904b), a third combiner (3904c), and one or more first dual-polarized antennas (3716c) (hereinafter, "first dual-polarized antennas (3716c)").

[0311] First Modulator (3708a-1), first Modulator (3708a-2), first Modulator (3708a-3), and the first The modulator (3708a-4) may be collectively referred to as the "first modulator (3708a)", and the second Modulator (3708b-1), second Modulator (3708b-2), second Modulator (3708b-3), and second The modulators (3708b-4) may be collectively referred to as "second modulators (3708b)." Although four of the modulators (3708) are shown in FIG. 39, it should be understood that the first modulators (3708a) and the second modulators (3708b) may include a predetermined number of modulators (3708) greater than or less than four.

[0312] Each of the first modulators (3708a) may be configured to generate a specific of the first transmission channel signals (3712a) having first data encoded in a first modulation format. In some implementations, each of the first modulators (3708a) may be configured to generate a specific of the first transmission channel signals (3712a), such that each of the first transmission channel signals (3712a) has one of a plurality of distinct first channel frequencies within the range of 300 GHz to 10 THz. In such implementations, the first modulators (3708a) may be described as performing "direct modulation". However, in other embodiments, each of the first modulators (3708a) may include an IF modulator configured to generate a specific of the first transmission channel signals (3712a) such that each of the first transmission channel signals (3712a) has one of a plurality of distinct first intermediate frequencies lower than a distinct first channel frequency of such first transmission channel signal (3712a). In such embodiments, each of the first modulators (3708a) may further include one or more first up-converters (not shown) configured to receive the first transmission channel signals (3712a) and up-convert the first transmission channel signals (3712a) such that each of the first transmission channel signals (3712a) has a distinct first channel frequency of such first transmission channel signal (3712a). In such embodiments, the first modulators (3708a) may be described as performing "IF modulation".

[0313] In some implementations, each of the first modulators (3708a) may be further configured to receive a first input signal pair (3724a), wherein each of the first input signal pairs (3724a) has a first input signal (3720a), a second input signal (3720b), and first data encoded in a first modulation format.

[0314] Each of the second modulators (3708b) may be configured to generate a specific of the second transmission channel signals (3712b) having second data encoded in the second modulation format. In some implementations, each of the second modulators (3708b) may be configured to generate a specific of the second transmission channel signals (3712b), wherein each of the second transmission channel signals (3712b) has one of a plurality of distinct second channel frequencies within the range of 300 GHz to 10 THz. In such implementations, the second modulators (3708b) may be described as performing "direct modulation". However, in other embodiments, each of the second modulators (3708b) may include an IF demodulator configured to generate a specific of the second transmission channel signals (3712b) such that each of the second transmission channel signals (3712b) has one of a plurality of distinct second intermediate frequencies lower than the distinct second channel frequency of such second transmission channel signals (3712b). In such embodiments, each of the second modulators (3708b) may further include one or more second up-converters (not shown) configured to receive the second transmission channel signals (3712b) and up-convert the second transmission channel signals (3712b) such that each of the second transmission channel signals (3712b) has the distinct channel frequency of such second transmission channel signals (3712b). In such embodiments, the second modulators (3708b) may be described as performing "IF modulation".

[0315] The first combiner (3904a) may be configured to receive first transmission channel signals (3712a) from first modulators (3708a) and to combine the first transmission channel signals (3712a) to become a first transmission WDM signal (3804a), and the second combiner (3904b) may be configured to receive second transmission channel signals (3712b) from second modulators (3708b) and to combine the second transmission channel signals (3712b) to become a second transmission WDM signal (3804b). A third combiner (3904c) may be configured to receive a first transmit WDM signal (3804a) and a second transmit WDM signal (3804b) and to combine the first transmit WDM signal (3804a) and the second transmit WDM signal (3804b) to become a transmit dual-polarization signal (3800). One or more of the first combiner (3904a), the second combiner (3904b), and the third combiner (3904c) may be multiplexers. In some implementations, one or more of the first combiner (3904a) and the second combiner (3904b) are WDM combiners, and the third combiner (3904c) is a polarization combiner.

[0316] The first dual-polarization antenna (3716c) may be configured to receive a transmitted dual-polarization signal (3800) from a third combiner (3904c) and to combine the transmitted dual-polarization signal (3800) (i.e., a first transmitted WDM signal (3804a) having a first polarization and a second transmitted WDM signal (3804b) having a second polarization) into a dual-polarization hollow waveguide (3704).

[0317] The receiver dual polarization network element (3902b) comprises a plurality of demodulators (3728) (e.g., the first shown in FIG. 39). Bokjogi (3728a-1), 2 Bokjogi (3728b-1), 1 Bokjogi (3728a-2), 2 Bokjogi (3728b-2), 1 Bokjogi (3728a-3), 2 Bokjogi (3728b-3), 1 Deborg (3728a-4), and the second It may include a demodulator (3728b-4), a first splitter (3912a), a second splitter (3912b), a third splitter (3912c), and one or more second dual-polarized antennas (3716d) (hereinafter, "second dual-polarized antennas (3716d)").

[0318] The second dual-polarization antenna (3716d) may be configured to receive a received dual-polarization signal (3800) (i.e., a first received WDM signal (3804a) having a first polarization and a second received WDM signal (3804b) having a second polarization) from a dual-polarization hollow waveguide (3704).

[0319] The third splitter (3912c) may be configured to receive a received dual-polarized signal (3800) from the second dual-polarized antenna (3716d) and to split the received dual-polarized signal (3800) into a first received WDM signal (3804a) and a second received WDM signal (3804b). The first splitter (3912a) may be configured to receive a first received WDM signal (3804a) from the third splitter (3912c) and to split the first received WDM signal (3804a) into a plurality of first received channel signals (3712a). The second splitter (3912b) may be configured to receive a second received WDM signal (3804b) from the third splitter (3912c) and to split the second received WDM signal (3804b) into a plurality of second received channel signals (3712b). One or more of the first splitter (3912a), the second splitter (3912b), and the third splitter (3912c) may be demultiplexers. In some implementations, one or more of the first splitter (3912a) and the second splitter (3912b) are WDM splitters, and the third splitter (3912c) is a polarization splitter.

[0320] First Bokjogi (3728a-1), 1 Bokjogi (3728a-2), 1 Deborg (3728a-3), and the first The demodulators (3728a-4) are collectively referred to as "first demodulators (3728a)", and the second Bokjogi (3728b-1), 2 Bokjogi (3728b-2), 2 Deborg (3728b-3), and the second The demodulators (3728b-4) are collectively referred to as "second demodulators (3728b)". Although four of the demodulators (3728) are shown in FIG. 39, it should be understood that the first demodulators (3728a) and the second demodulators (3728b) may include a predetermined number of demodulators (3728) greater or less than four.

[0321] Each of the first demodulators (3728a) may be configured to demodulate a specific of the first receiving channel signals (3712a) to produce first output signal pairs (3736a) configured for data detection and having first data encoded in a first modulation format. In some implementations, each of the first demodulators (3728a) may be configured to demodulate a specific of the first receiving channel signals (3712a) having one of a plurality of distinct first channel frequencies within the range of 300 GHz to 10 THz. However, in other embodiments, the receiver dual polarization network element (3902b) may further include one or more first down-converters (not shown) configured to receive first receiving channel signals (3712a) and down-convert the first receiving channel signals (3712a) such that each of the first receiving channel signals (3712a) has one of a plurality of distinct first intermediate frequencies lower than the distinct first channel frequency of such first receiving channel signals (3712a). In such embodiments, each of the first demodulators (3728a) may be configured to demodulate a specific of the first receiving channel signals (3712a) having one of a plurality of distinct first intermediate frequencies.

[0322] Each of the second demodulators (3728b) may be configured to demodulate a specific of the second receiving channel signals (3712b) to produce a second output signal pair (3736b) configured for data detection and having second data encoded in a second modulation format. In some implementations, each of the second demodulators (3728b) may be configured to demodulate a specific of the second receiving channel signals (3712b) having one of a plurality of distinct second channel frequencies within the range of 300 GHz to 10 THz. However, in another implementation, the second dual-polarization network element (3902b) may further include one or more second down-converters (not shown) configured to receive the second receiving channel signals (3712b) and down-convert the second receiving channel signals (3712b) such that each of the second receiving channel signals (3712b) has one of a plurality of distinct second intermediate frequencies lower than the distinct second channel frequency of the second receiving channel signals (3712b). In such implementations, each of the second demodulators (3728b) may be configured to demodulate a specific of the second receiving channel signals (3712b) having one of a plurality of distinct second intermediate frequencies.

[0323] Now, referring to FIG. 40, in some implementations, a transmitter dual-polarization network element (3902a) may include a first antenna (3716e) configured to transmit RF signals having a first polarization and a second antenna (3716f) configured to transmit RF signals having a second polarization. In such implementations, a receiver dual-polarization network element (3902b) may include a third antenna (3716g) configured to receive RF signals having a first polarization and a fourth antenna (3716h) configured to receive RF signals having a second polarization. Each of the first antenna (3716e), the second antenna (3716f), the third antenna (3716g), and the fourth antenna (3716h) may be a single-polarization antenna or a dual-polarization antenna.

[0324] Now, referring to FIG. 41, in some implementations, the transmitter dual-polarization network element (3902a) comprises a plurality of first antennas (3716e) (e.g., the first Antenna (3716e-1), first Antenna (3716e-2), first Antenna (3716e-3), and the first Antenna (3716e-4)) (collectively, "first antennas (3716e)") and a plurality of second antennas (3716f) (e.g., second Antenna (3716f-1), second Antenna (3716f-2), second Antenna (3716f-3), and second Antenna (3716f-4)) (collectively, "second antennas (3716f)") may be included.

[0325] Each of the first antennas (3716e) may be configured to receive a specific of the first transmission channel signals (3712a) and to apply a first polarization to a specific of the first transmission channel signals (3712a) as the specific of the first transmission channel signals (3712a) is coupled into a dual-polarized hollow waveguide (3704), and each of the second antennas (3716f) may be configured to receive a specific of the second transmission channel signals (3712b) and to apply a second polarization to a specific of the second transmission channel signals (3712b) as the specific of the second transmission channel signals (3712b) is coupled into a dual-polarized hollow waveguide (3704).

[0326] Similarly, in such implementations, the receiver dual-polarization network element (3902b) comprises a plurality of third antennas (3716g) (e.g., third Antenna (3716g-1), third Antenna (3716g-2), third Antenna (3716g-3), and third Antenna (3716g-4)) (collectively, "third antennas (3716g)") and a plurality of fourth antennas (3716h) (e.g., fourth Antenna (3716h-1), 4th Antenna (3716h-2), 4th Antenna (3716h-3), and the fourth Antenna (3716h-4)) (collectively, "fourth antennas (3716h)") may be included.

[0327] Each of the third antennas (3716g) may be configured to receive a specific of the first receiving channel signals (3712a) having a first polarization from the dual-polarized hollow waveguide (3704), and each of the fourth antennas (3716h) may be configured to receive a specific of the second receiving channel signals (3712b) having a second polarization from the dual-polarized hollow waveguide (3704).

[0328] Now, referring to FIG. 42, an exemplary implementation of the first modulator (3708a) illustrated in FIG. 37a is shown. However, it should be understood that any of the modulators (3708) described herein may be similar to the first modulator (3708a) as illustrated in FIG. 42. As illustrated in FIG. 42, the first modulator (3708a) comprises a transmitter local oscillator (LO) (4200) configured to generate a transmitter LO signal (4204), a transmitter phase shifter (4208) configured to receive the transmitter LO signal (4204) and shift the phase of the transmitter LO signal (4204) by a predetermined amount (e.g., 90°) to produce an orthogonal LO signal (4212), a first transmitter mixer (4216a) configured to receive the transmitter LO signal (4204) and a first input signal (3720a) and mix the transmitter LO signal (4204) with the first input signal (3720a) to produce a first transmitter mixer output signal (4220a), and a second input signal (3720b) ​​and the orthogonal LO signal (4212) to the second input It may include a second transmitter mixer (4216b) configured to produce a second transmitter mixer output signal (4220b) by mixing with a signal (3720b), and a transmitter adder (4224) configured to receive a first transmitter mixer output signal (4220a) and a second transmitter mixer output signal (4220b), and to produce a first transmitter channel signal (3712a) by combining the first transmitter mixer output signal (4220a) and the second transmitter mixer output signal (4220b).

[0329] As previously described, in some embodiments, the first modulator (3708a) may be configured to generate a first transmission channel signal (3712a) such that the first transmission channel signal (3712a) has a first channel frequency within the range of 300 GHz to 10 THz. However, in other embodiments, the first modulator (3708a) may be configured to generate a first transmission channel signal (3712a) such that the first transmission channel signal (3712a) has an intermediate frequency lower than the first channel frequency. In such embodiments, the first modulator (3708a) may further include one or more up-converters (not shown) configured to receive the first transmission channel signal (3712a) and up-convert the first transmission channel signal (3712a) such that the first transmission channel signal (3712a) has a first channel frequency.

[0330] Now, referring to FIG. 43, an exemplary implementation of the first demodulator (3728a) illustrated in FIG. 37b is shown. However, it should be understood that any of the demodulators (3728) described herein may be similar to the first demodulator (3728a) illustrated in FIG. 43. As illustrated in FIG. 43, the first demodulator (3728a) is configured to generate a receiver LO signal (4304) having an LO frequency within a predetermined range (e.g., within 1 GHz) of the first channel frequency of the RF carrier embedded in the first receiving channel signal (3712a) - a receiver LO (4300) which may be a voltage-controlled oscillator (VCO); a receiver phase shifter (4308) configured to receive the receiver LO signal (4304) and shift the phase of the receiver LO signal (4304) by a predetermined amount (e.g., 90°) to produce an orthogonal LO signal (4312); and to receive the receiver LO signal (4304) and the first receiving channel signal (3712a) and mix the receiver LO signal (4304) with the first receiving channel signal (3712a) to produce a first receiver mixer output signal (4320a). A first receiver mixer (4316a) configured to receive an orthogonal LO signal (4312) and a first receiving channel signal (3712a), and a second receiver mixer (4316b) configured to mix the orthogonal LO signal (4312) with the first receiving channel signal (3712a) to produce a second receiver mixer output signal (4320b), a first lowpass filter (LPF, 4324a) configured to receive the first receiver mixer output signal (4320a) and attenuate frequencies higher than a predetermined cutoff frequency to produce a first baseband signal (4322a) (also referred to herein as "U(t)" or "in-phase (I)" channel),A second LPF (4324b) configured to receive a second receiver mixer output signal (4320b) and attenuate frequencies higher than a predetermined cutoff frequency to produce a second baseband signal (4322b) (also referred to herein as a “V(t”) or “orthogonal (Q”) channel), a carrier recovery module (4332) configured to receive the first baseband signal (4322a) and the second baseband signal (4322b) and produce a carrier recovery control signal (4336) that causes the LO frequency and LO phase of the receiver LO signal (4304) to match the first channel frequency and first channel phase of the RF carrier embedded in the first receiver channel signal (3712a), A module (4340) having a circuit configured to form a pre-equalized output signal (4344) having a complex signal representation of, and It may include an equalizer (4348) configured to produce a first output signal (3732a) configured for data detection in a complex number form (i.e., having I and Q components) by equalizing a pre-equalized output signal (4344) by applying a plurality of complex tap weights having a complex signal representation. A complex number representation is mathematically convenient. The plurality of complex tap weights may be determined and / or adjusted based on a tap weight control algorithm such as Least Mean Squares (LMS), Zero Forcing (ZF), and / or similar. The operation of the equalizer (4348) can be described as a convolution between the input signal in the time domain (i.e., the pre-equalized output signal (4344)) and the equalizer transfer function (having a delay line finite impulse response (FIR) structure and multiple complex tap weights) or as a multiplication between the input signal in the frequency domain (i.e., the pre-equalized output signal (4344)) and the equalizer transfer function (having a delay line FIR structure and multiple complex tap weights). Those skilled in the art will understand that the equalizer transfer function can be determined based on multiple complex tap weights.

[0331] It should be understood that the above description generally refers to implementations in which one or more of the receiver network elements (3700a shown in FIG. 37b, 3902b shown in FIG. 39) include a coherent receiver. In other implementations, such as those in which one or more of the first modulation format and the second modulation format are DQPSK, the first demodulator (3728a) may not have one or more of the carrier recovery module (4332) and the receiver LO (4300); however, in such implementations, the first demodulator (3728a) may further include a differential detection circuit.

[0332] As previously described, in some embodiments, the first demodulator (3728a) may be configured to demodulate the first received channel signal (3712a) to produce a first output signal (3732a) such that the first output signal (3732a) has a first channel frequency within the range of 300 GHz to 10 THz. However, in other embodiments, the first demodulator (3728a) may additionally include one or more down-converters (not shown) configured to down-convert the first received channel signal (3712a) before demodulating the first received channel signal (3712a) to produce the first output signal (3732a) such that the first received channel signal (3712a) has an intermediate frequency lower than the first channel frequency. In such implementations, the first demodulator (3728a) may further include one or more down-converters (not shown) configured to receive the first receiving channel signal (3712a) and down-convert the first receiving channel signal (3712a) such that the first receiving channel signal (3712a) has an intermediate frequency lower than the first channel frequency.

[0333] Now, referring to FIG. 44, another exemplary embodiment of a receiver network element (3700b) configured according to the present disclosure is illustrated herein. The receiver network element (3700b) in the embodiment illustrated in FIG. 44 generally comprises a first part (4400a) and a second part (4400b). In some embodiments, the first part (4400a) is an X-polarized part, and the second part (4400b) is a Y-polarized part. In such embodiments, the first receiving channel signal (3712a) may be a received X-polarized signal (received X-pol signal), and the second receiving channel signal (3712b) may be a received Y-polarized signal (received Y-pol signal). As illustrated in FIG. 44, the receiver network element (3700b) may include a first demodulator (3728a), a second demodulator (3728b), and an equalizer (4402). As illustrated in FIG. 44, the equalizer (4402) may include a plurality of complex equalizers (4404) (e.g., the first complex equalizer (4404a), the second complex equalizer (4404b), the third complex equalizer (4404c), and the fourth complex equalizer (4404d) illustrated in FIG. 44) and a plurality of adders (4406) (e.g., the first adder (4406a) and the second adder (4406b) illustrated in FIG. 44).

[0334] It should be understood that while the first receiving channel signal (3712a) (i.e., X-polarized signal) and the second receiving channel signal (3712b) (i.e., Y-polarized signal) may use the same RF carrier, it may be necessary to include multiple carrier recovery modules (i.e., the first carrier recovery module (4332-1) and the second carrier recovery module (4332-2) shown in FIG. 44) within the receiver network element (3700b).

[0335] The operation of modules (4340-1) and (4340-2) of FIG. 44 is similar to that of module (4340) of FIG. 43. The first complex equalizer (4404a) receives the first pre-equalized output signal (4344-1) and the first complex tap weights calculated by the first demodulator (3728a). Receives, and the first pre-equalized output signal (4344-1) and the first complex tap weight It can be configured to produce the first intermediate signal (4408a) by multiplying it.

[0336] The second complex equalizer (4404b) uses the second pre-equalized output signal (4344-2) and the second complex tap weights calculated by the second demodulator (3728b). Received and the second pre-equalized output signal (4344-2) and the second complex tap weight It can be configured to produce a second intermediate signal (4408b) by multiplying it.

[0337] The third complex equalizer (4404c) uses the first pre-equalized output signal (4344-1) produced by the first demodulator (3728a) and the third complex tap weight Receives the first pre-equalized output signal (4344-1) and the third complex tap weight It can be configured to produce a third intermediate signal (4408c) by multiplying it.

[0338] The fourth complex equalizer (4404d) uses the second pre-equalized output signal (4344-2) produced by the second demodulator (3728b) and the fourth complex tap weight Received and the second pre-equalized output signal (4344-2) and the fourth complex tap weight It can be configured to produce the fourth intermediate signal (4408d) by multiplying it.

[0339] The first adder (4406a) may be configured to receive a first equalizer intermediate signal (4408a) produced by a first complex equalizer (4404a) and a second equalizer intermediate signal (4408b) produced by a second complex equalizer (4404b), and to add the first equalizer intermediate signal (4408a) and the second equalizer intermediate signal (4408b) to produce a first output signal (3732a). In some implementations, the first output signal (3732a) is an equalized X-polarized signal.

[0340] The second adder (4406b) may be configured to receive the third equalizer intermediate signal (4408c) produced by the third complex equalizer (4404c) and the fourth equalizer intermediate signal (4408d) produced by the fourth complex equalizer (4404d), and to add the third equalizer intermediate signal (4408c) and the fourth equalizer intermediate signal (4408d) to produce a second output signal (3732b). In some implementations, the second output signal (3732b) is an equalized Y-polarized signal.

[0341] If the system's cross-pol discrimination is outside a predetermined range (e.g., 16 dB to 25 dB, depending on the modulation format used and the system link budget), the second complex tap weight and third complex tap weights It should be understood that it can be set to zero, which will cause the first part (4400a) and the second part (4400b) of the receiver network element (3700b) of FIG. 44 to operate as two separate single-polarization receiver network elements as shown in FIG. 43. In such a case, the receiver network element (3700b) can operate more efficiently and thereby consume less power.

[0342] It should be understood that the implementation of the first demodulator (3728a) shown in FIG. 43 and the implementation of the receiver network element (3700b) shown in FIG. 44 are exemplary implementations provided as examples. It should also be understood that the aforementioned approach may be referred to as an "analog approach." Conversely, a "digital approach" may also be used instead, which may include one or more ADCs and digital signal processors (DSPs) configured to perform the demodulation and equalization described herein.

[0343] In some embodiments, the first demodulator (3728a) and the second demodulator (3728b) may be configured to each demodulate the first channel signal (3712a) and the second channel signal (3712b) to produce the first input signal (3720a) and the second input signal (3720b), wherein the first input signal (3720a) has a first channel frequency in the range of 300 GHz to 10 THz and the second input signal (3720b) ​​has a second channel frequency in the range of 300 GHz to 10 THz. However, in other embodiments, the first demodulator (3728a) may be configured to downconvert the first channel signal (3712a) before demodulating the first channel signal (3712a) to produce the first input signal (3720a), such that the first channel signal (3712a) has an intermediate frequency lower than the first channel frequency. In such embodiments, the first demodulator (3728a) may further include one or more downconverters (not shown) configured to receive the first channel signal (3712a) and downconvert the first channel signal (3712a) such that the first channel signal (3712a) has an intermediate frequency lower than the first channel frequency. Similarly, in such implementations, the second demodulator (3728b) may be configured to downconvert the second channel signal (3712b) so that the second channel signal (3712b) has an intermediate frequency lower than the second channel frequency before demodulating the second channel signal (3712b) to produce the second input signal (3720b). In such implementations, the second demodulator (3728b) may further include one or more downconverters (not shown) configured to receive the second channel signal (3712b) and downconvert the second channel signal (3712b) so that the second channel signal (3712b) has an intermediate frequency lower than the second channel frequency.

[0344] Now, referring to FIG. 45, an exemplary implementation of a method of use (4500) according to the present disclosure is illustrated therein. As illustrated in FIG. 45, the method (4500) generally comprises: coupling a first wavelength division multiplexed (WDM) signal (3804a) as a first polarization into a hollow waveguide, e.g., a dual-polarized hollow waveguide (3704), by means of one or more antennas (900, 3716), and coupling a second WDM signal (3804b) as a second polarization into a hollow waveguide, e.g., a dual-polarized hollow waveguide (3704), thereby propagating RF signals having the first polarization and the second polarization simultaneously through the dual-polarized hollow waveguide (3704) - wherein the first WDM signal (3804a) has a first channel frequency in the range of 300 GHz to 10 THz, and the second WDM signal (3804b) has a second channel frequency in the range of 300 GHz to 10 THz - (step Includes 4504).

[0345] In some implementations, the step (step 4504) of combining the first WDM signal (3804a) and the second WDM signal (3804b) into a dual-polarized hollow waveguide (3704) comprises: combining the first WDM signal (3804a) and the second WDM signal (3804b) having a modulation format selected from the group consisting of IM / DD (IM(intensity-modulation) / DD(direct-detection)); NRZ (non-return-to-zero modulation); PAMn (pulse-amplitude-modulation); IM-PAMn; mQAM (m-quadrature-amplitude-modulation); QPSK (quadrature-phase-shift-keying); DQPSK (differential-detection QPSK); and SSB (single-sideband modulation):

[0346] In some implementations, the step (step 4504) of combining the first WDM signal (3804a) and the second WDM signal (3804b) into a dual-polarized hollow waveguide (3704) includes combining the first WDM signal (3804a) to a first antenna (3716e) configured to impart a first polarization and combining the second WDM signal (3804b) to a second antenna (3716f) configured to impart a second polarization, wherein the first antenna (3716e) is separate from the second antenna (3716f).

[0347] In some implementations, the first polarization is left-hand circular polarization (LHCP) and the second polarization is right-hand circular polarization (RHCP). In some implementations, the first polarization is horizontal linear polarization (HLP) and the second polarization is vertical linear polarization (VLP).

[0348] In some implementations, the step of combining the first WDM signal (3804a) and the second WDM signal (3804b) into a dual-polarized hollow waveguide (3704) (step 4504) includes combining the first WDM signal (3804a) and the second WDM signal (3804b) into a dual-polarized antenna (e.g., a first dual-polarized antenna (3716c)) configured to simultaneously transmit RF signals having the first polarization and the second polarization into the dual-polarized hollow waveguide (3704).

[0349] In some embodiments, the method (4500) further comprises the step of combining a plurality of first channel signals (3712a) to form a first WDM signal (3804a), wherein the first channel signals have a plurality of channel frequencies in the range of 300 GHz to 10 THz, and at least some of the first channel signals are encoded as data. In some such embodiments, the spacing between adjacent first channel signals (3712a) is in the range of 50 GHz to 400 GHz.

[0350] Now, referring to FIG. 46a, another exemplary embodiment of a network element (4600) configured according to the present disclosure is illustrated herein. As illustrated in FIG. 46a, the network element (4600) generally comprises one or more demodulators (4604) (hereinafter “demodulators (4604)”) and one or more modulators (4608) (hereinafter “modulators (4608)”) coupled together by one or more buses or electrical circuits as illustrated in FIG. 46a.

[0351] A demodulator (4604) may be configured to receive one or more input signals (4612) (hereinafter, "input signals (4612)"), such as the first input signal (4612a) and the second input signal (4612b) shown in FIG. 46a, and to extract a series of phase signals (4616) (hereinafter, "phase signals (4616)") and a series of amplitude signals (4620) (hereinafter, "amplitude signals (4620)") from the input signals (4612). The demodulator (4604) may be configured to decompose the input signals (4612) into individual bitstreams and to produce the phase signals (4616) and amplitude signals (4620) based on the individual bitstreams. Accordingly, the demodulator (4604) may be configured to extract a first phase signal (4616a) and a first amplitude signal (4620a) from a first input signal (4612a). Similarly, the demodulator (4604) may be configured to extract a second phase signal (4616b) and a second amplitude signal (4620b) from a second input signal (4612b).

[0352] The input signals (4612) may have input data encoded therein. For example, the first input signal (4612a) may have first input data encoded therein, and the second input signal (4612b) may have second input data encoded therein. As described in more detail below, the first input data and the second input data may be encoded in the first input signal (4612a) and the second input signal (4612b), respectively, according to a first modulation format which may be a pulse amplitude modulation (PAMn) format.

[0353] The modulator (4608) receives phase signals (4616) and amplitude signals (4620) and modulates the phase signals (4616) and amplitude signals (4620) representing first and second input data onto an output signal (4624), wherein the output signal (4624) may be configured to have the first and second input data encoded in a second modulation format. The output signal (4624) may have a carrier frequency within the THz frequency band (104). In some implementations, the carrier frequency is within the range of 500 GHz to 10 THz. As described in more detail below, the modulator (4608) may be further configured to receive or generate a local oscillator (LO) signal (5012) (illustrated in FIG. 50a and FIG. 50b), which is an electrical signal in the range of 500 GHz to 10 THz, and phase signals (4616) and amplitude signals (4620) are modulated onto this LO signal to produce an output signal (4624). Also, as described in more detail below, the second modulation format may be different from the first modulation format.

[0354] In some implementations, the first modulation format is the PAMn (pulse-amplitude-modulation-n) format and the second modulation format is the mQAM (m-quadrature-amplitude-modulation) format. In some such implementations, the first modulation format is the PAM4 (pulse-amplitude-modulation-4) format and the second modulation format is the 16QAM (16-quadrature-amplitude-modulation) format. However, in other implementations, the first modulation format and the second modulation format may be modulation formats other than PAMn, PAM4, mQAM, or 16QAM.

[0355] Now, referring to FIG. 46b, another exemplary embodiment of a network element (4600) configured according to the present disclosure is illustrated herein. As illustrated in FIG. 46b, in some embodiments, the network element (4600) further comprises an antenna (4628) configured to receive an output signal (4624) and couple the output signal (4624) into a hollow waveguide (4632). In some embodiments, the hollow waveguide (4632) is a fiber (hollow or solid) configured to propagate electromagnetic waves in the THz frequency band (104). The antenna (4628) is coupled to a modulator (4608) by one or more signal paths, which may be a bus or an electrical circuit.

[0356] Now, referring to FIG. 47a, an exemplary embodiment of a demodulator (4604) configured according to the present disclosure is illustrated herein. As illustrated in FIG. 47a, the demodulator (4604) may include a first splitter (4700a) and a second splitter (4700b) coupled together by one or more buses or electrical circuits as illustrated in FIG. 47a, one or more phase demodulators (4704) (hereinafter, "phase demodulators (4704)"), and one or more amplitude demodulators (4708) (hereinafter, "amplitude demodulators (4708)").

[0357] The first splitter (4700a) and the second splitter (4700b) may be configured to receive the first input signal (4612a) and the second input signal (4612b) respectively, and to divide the first input signal (4612a) and the second input signal (4612b) respectively into at least two pre-demodulated signals (4712) (hereinafter, "pre-demodulated signals (4712)"). For example, the first splitter (4700a) may be configured to receive the first input signal (4612a) and split the first input signal (4612a) into the first pre-demodulated signal (4712a) and the second pre-demodulated signal (4712b) shown in FIG. 47a, and the second splitter (4700b) may be configured to receive the second input signal (4612b) and split the second input signal (4612b) into the third pre-demodulated signal (4712c) and the fourth pre-demodulated signal (4712d) shown in FIG. 47a.

[0358] The phase demodulators (4704) may include a first phase demodulator (4704a) and a second phase demodulator (4704b). The first phase demodulator (4704a) may be configured to extract a series of first phase signals (4616a) from a first pre-demodulated signal (4712a), and the second phase demodulator (4704b) may be configured to extract a series of second phase signals (4616b) from a third pre-demodulated signal (4712c), such that the first phase signals (4616a) are synchronized with the second phase signals (4616b) and can be used to represent input data encoded within the input signals (4612).

[0359] Amplitude demodulators (4708) may include a first amplitude demodulator (4708a) and a second amplitude demodulator (4708b). The first amplitude demodulator (4708a) may be configured to extract a first amplitude signal (4620a) from a second pre-demodulated signal (4712b), and the second amplitude demodulator (4708b) may be configured to extract a second amplitude signal (4620b) from a fourth pre-demodulated signal (4712d).

[0360] Now, referring to FIG. 47b, another exemplary embodiment of a demodulator (4604a) configured according to the present disclosure is illustrated herein. As illustrated in FIG. 47b, the demodulator (4604a) may include a clock-and-data-recovery circuit (CDR) (4716) configured to extract a first phase signal (4616a) and a first amplitude signal (4620a) from a first input signal (4612a) and to extract a second phase signal (4616b) and a second amplitude signal (4620b) from a second input signal (4612b). That is, the CDR circuit (4716) may be configured to decompose input signals (4612) into individual bit streams, as described above with the demodulator (4604), and to produce phase signals (4616) and amplitude signals (4620) based on the individual bit streams. As described herein, the CDR circuit (4716) may be similar to a conventional CDR circuit in that the CDR circuit (4716) of the present disclosure receives input signals (4612) (e.g., PAM4 signals); however, unlike a conventional CDR circuit that can provide signals (e.g., PAM4 signals) having the same modulation format as outputs, the CDR circuit (4716) of the present disclosure can provide phase signals (4616) and amplitude signals (4620) as outputs.

[0361] Now, referring to FIG. 48, an exemplary embodiment of a first phase demodulator (4704a) configured according to the present disclosure is illustrated herein. However, it should be understood that any one of the phase demodulators (4704) described herein may be similar in form and function to the first phase demodulator (4704a) illustrated in FIG. 48. As illustrated in FIG. 48, the first phase demodulator (4704a) may include an amplifier (4800), a first alternating current (AC) coupler (4804a), and a first comparator (4808a), which are coupled together by one or more buses or electrical circuits as illustrated in FIG. 48.

[0362] The amplifier (4800) may be configured to receive a first pre-demodulated signal (4712a) (in electrical form) and limit the amplitude of the first pre-demodulated signal (4712a) to produce an amplitude-limiting signal (4812) (in electrical form). In some implementations, the amplifier (4800) is a limiting amplifier.

[0363] The first AC coupler (4804a) may be configured to receive an amplitude limiting signal (4812), block the passage of direct current (DC) signals while allowing the passage of AC signals, thereby removing any DC offset from the amplitude limiting signal (4812) to produce a first threshold center signal (4816a), wherein the first threshold center signal (4816a) is formed around a predetermined threshold voltage. In some embodiments, the predetermined threshold voltage is zero.

[0364] The first comparator (4808a) may be configured to receive the first threshold center signal (4816a) and determine the polarity (i.e., positive or negative) of the first threshold center signal (4816a) to produce the first phase signal (4616a) (in electrical form). In some implementations, the first comparator (4808a) is a sign check comparator.

[0365] Now, referring to FIG. 49, an exemplary embodiment of a first amplitude demodulator (4708a) configured according to the present disclosure is illustrated herein. However, it should be understood that any of the amplitude demodulators (4708) described herein may be similar in form and function to the first amplitude demodulator (4708a) illustrated in FIG. 49. As illustrated in FIG. 49, the first amplitude demodulator (4708a) may include a magnitude extraction circuit (4900), a second AC coupler (4804b), and a second comparator (4808b), which are coupled together by one or more buses or electrical circuits as illustrated in FIG. 49.

[0366] The magnitude extraction circuit (4900) may be configured to receive a second pre-demodulated signal (4712b) (in electrical form) and determine the amplitude of the second pre-demodulated signal (4712b) to produce a rectified signal (4904) (in electrical form). In some embodiments, the magnitude extraction circuit (4900) is a rectifier. In other embodiments, the magnitude extraction circuit (4900) may be, for example, a square circuit.

[0367] The second AC coupler (4804b) may be configured to receive a rectified signal (4904) (in electrical form), block the passage of DC signals while allowing the passage of AC signals, thereby removing any DC offset from the rectified signal (4904) to produce a second threshold center signal (4816b) (in electrical form), wherein the second threshold center signal (4816b) is formed around a predetermined threshold voltage. In some implementations, the predetermined threshold voltage is zero.

[0368] The second comparator (4808b) may be configured to receive the second threshold center signal (4816b) and determine the polarity (i.e., positive or negative) of the second threshold center signal (4816b) to produce a first amplitude signal (4620a) (in electrical form). That is, if the polarity of the second threshold center signal (4816b) is positive, the first amplitude signal (4620a) may have a non-zero value (e.g., 1), and if the polarity of the second threshold center signal (4816b) is negative, the first amplitude signal (4620a) may have a zero value (i.e., 0). In some implementations, the second comparator (4808b) is a sign check comparator.

[0369] Now, referring to FIG. 50a, an exemplary embodiment of a modulator (4608) configured according to the present disclosure is illustrated herein. As illustrated in FIG. 50a, the modulator (4608) may include a third splitter (4700c), a first phase modulator (5000a), a second phase modulator (5000b), a first amplitude modulator (5004a), a second amplitude modulator (5004b), and a combiner (5008), which are combined together by one or more buses or electrical circuits as illustrated in FIG. 50.

[0370] The third splitter (4700c) may be configured to receive an LO signal (5012) generated by an LO generator (not shown) outside the modulator (4608) and to split the LO signal (5012) into one or more unmodulated carrier signals (5016) (in electrical form) (hereinafter referred to as "unmodulated carrier signals"). That is, the third splitter (4700c) may be configured to receive the LO signal (5012) and to split the LO signal (5012) into a first unmodulated carrier signal (5016a) (in electrical form) and a second unmodulated carrier signal (5016b) (in electrical form) as illustrated in FIG. 50a. In some implementations, the first unmodulated carrier signal (5016a) can represent the I component of the output signal (4624), and the second unmodulated carrier signal (5016b) can represent the Q component of the output signal (4624).

[0371] The first phase modulator (5000a) may be configured to receive a first unmodulated carrier signal (5016a) (i.e., the I component of the output signal (4624)) and a first phase signal (4616a), and to modulate the first phase signal (4616a) onto the first unmodulated carrier signal (5016a) to produce a first phase-modulated carrier signal (5020a). The first amplitude modulator (5004a) may be configured to receive the first phase-modulated carrier signal (5020a) and a first amplitude signal (4620a), and to modulate the first amplitude signal (4620a) onto the first phase-modulated carrier signal (5020a) to produce a first phase-amplitude-modulated carrier signal (5024a).

[0372] The second phase modulator (5000b) may be configured to receive the second unmodulated carrier signal (5016b) (i.e., the Q component of the output signal (4624)) and the second phase signal (4616b), and to modulate the second phase signal (4616b) onto the second unmodulated carrier signal (5016b) to produce the second phase-modulated carrier signal (5020b). The second amplitude modulator (5004b) may be configured to receive the second phase-modulated carrier signal (5020b) and the second amplitude signal (4620b), and to modulate the second amplitude signal (4620b) onto the second phase-modulated carrier signal (5020b) to produce the second phase-amplitude-modulated carrier signal (5024b).

[0373] The combiner (5008) may be configured to receive a first phase amplitude modulated carrier signal (5024a) and a second phase amplitude modulated carrier signal (5024b), and to combine the first phase amplitude modulated carrier signal (5024a) and the second phase amplitude modulated carrier signal (5024b) to produce an output signal (4624), wherein the output signal (4624) is encoded in a second modulation format.

[0374] In some implementations, the LO signal (5012) has an LO frequency equal to the carrier frequency (i.e., a frequency within the range of 500 GHz to 10 THz). However, in other implementations, the LO signal (5012) has an LO frequency lower than the carrier frequency. In such implementations, the combiner (5008) is configured to receive a first phase amplitude modulated carrier signal (5024a) and a second phase amplitude modulated carrier signal (5024b), and to combine the first phase amplitude modulated carrier signal (5024a) and the second phase amplitude modulated carrier signal (5024b) to produce an intermediate signal (not shown) having an LO frequency, and the network element (4600) further includes an upconverter (not shown) configured to receive the intermediate signal and upconvert the intermediate signal to produce an output signal (4624) (in electrical form) having a carrier frequency. In other embodiments, the LO signal (5012) has an LO frequency higher than the carrier frequency. In such embodiments, the combiner (5008) is configured to receive a first phase amplitude modulated carrier signal (5024a) and a second phase amplitude modulated carrier signal (5024b), and to combine the first phase amplitude modulated carrier signal (5024a) and the second phase amplitude modulated carrier signal (5024b) to produce an intermediate signal (not shown) having an LO frequency, and the network element (4600) further includes a downconverter (not shown) configured to receive the intermediate signal and downconvert the intermediate signal to produce an output signal (4624) (in electrical form) having a carrier frequency.

[0375] Now, referring to FIG. 50b, another exemplary embodiment of a modulator (4608a) configured according to the present disclosure is illustrated herein. As illustrated in FIG. 50b, in some embodiments, a third splitter (4700c) is electrically coupled to an LO generator (5028) to receive an LO signal (5012) (in electrical form) from the LO generator (5028) located inside the modulator (4608a).

[0376] In some embodiments, one or more of the first phase modulator (5000a) and the second phase modulator (5000b) include a crossbar switch (5200) (shown in FIG. 52) configured to select either a 0° signal or a 180° signal. In some embodiments, one or more of the first amplitude modulator (5004a) and the second amplitude modulator (5004b) include a switched attenuator (e.g., a PI-type attenuator (5300a) shown in FIG. 53a, a T-type attenuator (5300b) shown in FIG. 53b, and a bridge-type T-type attenuator (5300c) shown in FIG. 53c) configured to produce signals having either a first amplitude level or a second amplitude level. In other implementations, one or more of the first amplitude modulator (5004a) and the second amplitude modulator (5004b) include one of a switched amplifier and a variable gain amplifier.

[0377] In some implementations, the first amplitude level is 1 V and the second amplitude level is 3 V. However, in other implementations, the first amplitude level is a predetermined number of volts greater than or less than 1, and the second amplitude level is a predetermined number of volts greater than or less than 3. In such implementations, the first amplitude level may be a fraction of the second amplitude level (e.g., 1 / 4, 1 / 3, or 1 / 2).

[0378] Now, referring to FIG. 51, an exemplary implementation of a method (5100) for performing direct modulation from a first modulation format to a second modulation format in a THz frequency band (104) is illustrated herein. As illustrated in FIG. 51, the method (5100) comprises: receiving a first input signal (4612a) and a second input signal (4612b) by a demodulator (4604) - the first input signal (4612a) has first input data, the second input signal (4612b) has second input data, and the first input data and the second input data are encoded in a first modulation format - (step (5104)); By means of a demodulator (4604), a first phase signal (4616a) and a first amplitude signal (4620a) are extracted from a first input signal (4612a), and a second phase signal (4616b) and a second amplitude signal (4620b) are extracted from a second input signal (4612b) (step (5108)); by means of a modulator (4608), the first phase signal (4616a), the first amplitude signal (4620a), the second phase signal (4616b), and the second amplitude signal (4620b) are modulated onto an output signal (4624), such that the output signal (4624) is encoded in a second modulation format - the output signal (4624) has a carrier frequency within the range between 500 GHz and 2 THz - (step (5112)); The method includes steps of converting an output signal (4624) from an electrical signal into an electromagnetic wave by means of an antenna (4628) (step (5114)); and coupling the electromagnetic wave to a hollow waveguide (4632) by means of an antenna (4628) (step (5116)).

[0379] In some implementations, the step of receiving the first input signal (4612a) and the second input signal (4612b) (step (5104)) is further defined as the step of receiving the first input signal (4612a) and the second input signal (4612b) by the demodulator (4604), wherein the first input signal (4612a) has first input data and the second input signal (4612b) has second input data, and the first input data and the second input data are encoded in a first modulation format, wherein the first modulation format is a PAMn (e.g., PAM4) format.

[0380] In some implementations, the step (step 5108) of extracting a first phase signal (4616a) and a first amplitude signal (4620a) from a first input signal (4612a) and a second phase signal (4616b) and a second amplitude signal (4620b) from a second input signal (4612b) is further defined as a step of extracting a first phase signal (4616a) and a first amplitude signal (4620a) from a first input signal (4612a) and a second phase signal (4616b) and a second amplitude signal (4620b) from a second input signal (4612b) by a demodulator (4604), wherein the demodulator (4604) includes a CDR circuit (4716).

[0381] In some implementations, the step (step 5108) of extracting a first phase signal (4616a) and a first amplitude signal (4620a) from a first input signal (4612a) and a second phase signal (4616b) and a second amplitude signal (4620b) from a second input signal (4612b) comprises: splitting the first input signal (4612a) by a first splitter (4700a) to become a first pre-demodulated signal (4712a) and a second pre-demodulated signal (4712b); and splitting the second input signal (4612b) by a second splitter (4700b) to become a third pre-demodulated signal (4712c) and a fourth pre-demodulated signal (4712d). The method further includes the step of extracting a first phase signal (4616a) from a first pre-demodulated signal (4712a) by a first phase demodulator (4704a); the step of extracting a first amplitude signal (4620a) from a second pre-demodulated signal (4712b) by a first amplitude demodulator (4708a); the step of extracting a second phase signal (4616b) from a third pre-demodulated signal (4712c) by a second phase demodulator (4704b); and the step of extracting a second amplitude signal (4620b) from a fourth pre-demodulated signal (4712d) by a second amplitude demodulator (4708b).

[0382] In some implementations, the step (step 5108) of extracting a first phase signal (4616a) and a first amplitude signal (4620a) from a first input signal (4612a) and a second phase signal (4616b) and a second amplitude signal (4620b) from a second input signal (4612b) comprises: extracting the first phase signal (4616a) from the first pre-demodulated signal (4712a) by the first phase demodulator (4704a) by transmitting the first pre-demodulated signal (4712a) to an amplifier (4800) having an output connected to the input of a first comparator (4808a); A step of extracting a first amplitude signal (4620a) from a second pre-demodulated signal (4712b) by a first amplitude demodulator (4708a) by transmitting the second pre-demodulated signal (4712b) to a magnitude extraction circuit (4900) having an output connected to the input of a second comparator (4808b); a step of extracting a second phase signal (4616b) from a third pre-demodulated signal (4712c) by a second phase demodulator (4704b) by transmitting the third pre-demodulated signal (4712c) to an amplifier (4800) having an output connected to the input of a first comparator (4808a); and is further defined as a step of extracting a second amplitude signal (4620b) from a fourth pre-demodulated signal (4712d) by a second amplitude demodulator (4708b) by transmitting the fourth pre-demodulated signal (4712d) to a magnitude extraction circuit (4900) having an output connected to the input of a second comparator (4808b).

[0383] In some implementations, the step (step (5112)) of modulating the first phase signal (4616a), the first amplitude signal (4620a), the second phase signal (4616b), and the second amplitude signal (4620b) onto the output signal (4624) is further defined as the step of modulating the first phase signal (4616a), the first amplitude signal (4620a), the second phase signal (4616b), and the second amplitude signal (4620b) onto the output signal (4624) by a modulator (4608) such that the output signal (4624) is encoded in a second modulation format, wherein the output signal (4624) has a carrier frequency in the range of 500 GHz to 2 THz, and the second modulation format is an mQAM (e.g., 16QAM) format.

[0384] In some implementations, the step (step 5112) of modulating the first phase signal (4616a), the first amplitude signal (4620a), the second phase signal (4616b), and the second amplitude signal (4620b) onto the output signal (4624) comprises: the step of splitting the LO signal (5012) by the third splitter (4700c) to become the first unmodulated carrier signal (5016a) and the second unmodulated carrier signal (5016b); and the step of modulating the first phase signal (4616a) onto the first unmodulated carrier signal (5016a) by the first phase modulator (5000a). A step of modulating a first amplitude signal (4620a) onto a first unmodulated carrier signal (5016a) (i.e., a first phase-modulated carrier signal (5020a)) by a first amplitude modulator (5004a); a step of modulating a second phase signal (4616b) onto a second unmodulated carrier signal (5016b) by a second phase modulator (5000b); a step of modulating a second amplitude signal (4620b) onto a second unmodulated carrier signal (5016b) (i.e., a second phase-modulated carrier signal (5020b)) by a second amplitude modulator (5004b); The method further includes the step of combining a first non-modulated carrier signal (5016a) (i.e., a first phase amplitude modulated carrier signal (5024a)) and a second non-modulated carrier signal (5016b) (i.e., a second phase amplitude modulated carrier signal (5024b)) by means of a combiner (5008) to form an output signal (4624), wherein the output signal (4624) is encoded in a second modulation format.

[0385] In some implementations, the step (step 5112) of modulating the first phase signal (4616a), the first amplitude signal (4620a), the second phase signal (4616b), and the second amplitude signal (4620b) onto the output signal (4624) comprises: splitting the LO signal (5012) by a third splitter (4700c) to become a first unmodulated carrier signal (5016a) and a second unmodulated carrier signal (5016b); modulating the first amplitude signal (4620a) onto the first unmodulated carrier signal (5016a) by a first amplitude modulator (5004a); and modulating the first phase signal (4616a) onto the first unmodulated carrier signal (5016a) by a first phase modulator (5000a). The method further includes the step of modulating the second amplitude signal (4620b) onto the second unmodulated carrier signal (5016b) by means of a second amplitude modulator (5004b); the step of modulating the second phase signal (4616b) onto the second unmodulated carrier signal (5016b) by means of a second phase modulator (5000b); and the step of combining the first unmodulated carrier signal (5016a) and the second unmodulated carrier signal (5016b) by means of a combiner (5008) to form an output signal (4624), wherein the output signal (4624) is encoded in the second modulation format.

[0386] In some implementations, the step (step 5112) of modulating the first phase signal (4616a), the first amplitude signal (4620a), the second phase signal (4616b), and the second amplitude signal (4620b) onto the output signal (4624) comprises: the step of modulating the first phase signal (4616a) onto the first unmodulated carrier signal (5016a) by the first phase modulator (5000a) - wherein the first phase modulator (5000a) is the first crossbar switch -; the step of modulating the first amplitude signal (4620a) onto the first unmodulated carrier signal (5016a) (i.e., the first phase modulated carrier signal (5020a)) by the first amplitude modulator (5004a) - wherein the first amplitude modulator (5004a) is the first switched attenuator -; and is further defined as the step of modulating the second phase signal (4616b) onto the second unmodulated carrier signal (5016b) by the second phase modulator (5000b) - wherein the second phase modulator (5000b) is a second crossbar switch -; and the step of modulating the second amplitude signal (4620b) onto the second unmodulated carrier signal (5016b) (i.e., the second phase modulated carrier signal (5020b)) by the second amplitude modulator (5004b) - wherein the second amplitude modulator (5004b) is a second switched attenuator -.

[0387] Now, referring to FIG. 54, another exemplary embodiment of a transceiver (5400a) configured according to the present disclosure is illustrated therein.

[0388] Now, referring to FIG. 55, another exemplary embodiment of a transceiver (5400b) configured according to the present disclosure is illustrated therein.

[0389] Now, referring to FIG. 56, another exemplary embodiment of a transceiver (5400c) configured according to the present disclosure is illustrated therein.

[0390] Now, referring to FIG. 57, another exemplary embodiment of a transmitter (5700a) configured according to the present disclosure is illustrated therein.

[0391] Now, referring to FIG. 58, another exemplary embodiment of a receiver (5800) configured according to the present disclosure is illustrated therein.

[0392] Now, referring to FIG. 59, another exemplary embodiment of a transmitter (5700b) configured according to the present disclosure is illustrated therein.

[0393] Now, referring to FIG. 60, another exemplary embodiment of a transmitter (5700c) configured according to the present disclosure is illustrated therein.

[0394] Now, referring to FIGS. 61 through 63, exemplary embodiments of differential circuits configured according to the present disclosure are shown, which include a first differential circuit (6100a) (shown in FIG. 61), a second differential circuit (6100b) (shown in FIG. 62), and a third differential circuit (6100c) (shown in FIG. 63).

[0395] Now, referring to FIG. 64, an exemplary implementation of an antenna array (6400) configured according to the present disclosure is illustrated therein.

[0396] Now, referring to FIG. 65, a perspective view of an exemplary embodiment of an antenna (6500) configured and used according to the present disclosure is shown. As illustrated in FIG. 65, the antenna (6500) comprises an electromagnetic absorber (6502) positioned around one or more radiators (6504) (e.g., a first radiator (6504a), a second radiator (6504b), a third radiator (6504c), and a fourth radiator (6504d)). One or more radiators (6504) may be configured according to the radiator (908) as described in detail above. Although four radiators (6504) are illustrated in FIG. 65, it should be understood that the antenna (6500) may include more or fewer than four radiators (6504), such as (e.g.) one radiator (6504) or eight radiators (6504).

[0397] In one embodiment, one or more of the radiators (6504) may be mounted on their respective ground planes (904a to 904d). For example, a first radiator (6504a) may be mounted on the first ground plane (904a), a second radiator (6504b) may be mounted on the second ground plane (904b), a third radiator (6504c) may be mounted on the third ground plane (904c), and a fourth radiator (6504d) may be mounted on the fourth ground plane (904d) (not shown).

[0398] In some embodiments, one or more of the radiators (6504) may be placed within a hollow waveguide (208) (not shown in FIG. 65). In other embodiments, one or more of the radiators (6504) may be placed coaxially away from the hollow waveguide (208). In some embodiments, one or more of the radiators (6504) may be coupled to a fiber-coupled RF transmitter (such as the first transmitter (212a)), while the other radiators (6504) may be coupled to a fiber-coupled RF receiver (such as the first receiver (216a)).

[0399] In one embodiment, the electromagnetic absorber (6502) is not positioned between the radiators (6504) (e.g., first radiator (6504a), second radiator (6504b), third radiator (6504c), fourth radiator (6504d)) and the hollow waveguide (208). In some embodiments, the electromagnetic absorber (6502) may include a distal surface (6508), an opposed proximal surface (6509), and one or more openings (6510) formed on the distal surface (6508) and extending toward the opposed proximal surface (6509). In the embodiment illustrated in FIG. 11, four openings (6510) are illustrated as an example, with one of the radiators (6504) located within each of the four openings (6510).

[0400] In some non-limiting embodiments, only one of the radiators (6504) is located within a specific of the openings (6510). The electromagnetic absorber (6502) has a plurality of inner surfaces (6511) defining the openings (6510). Each of the inner surfaces (6511) surrounds one of the radiators (6504) located within its respective opening (6510). In the illustrated example, the electromagnetic absorber (6502) has no cover covering any of the openings (6510) so that electromagnetic waves generated by the radiators (6504a to 6504d) are transmitted directly into the hollow waveguide (208). In embodiments incorporating a cover over one or more of the openings (6510), the cover may be selected from a material that is transparent to (or mostly transparent to) electromagnetic waves. For example, the cover may comprise a plastic material. The cover can cause less than 10% of the reflected power of the electromagnetic waves. The opposite proximal surface (6509) may be located adjacent to the ground planes (90a-d). In some embodiments, the opposite proximal surface (6509) is in contact with the ground planes (90a-d).

[0401] In one embodiment, each of the openings (6510) may have a cross-sectional shape similar in shape to the radiators (6504). In some embodiments, the cross-sectional shape of the openings (6510) may be positioned away from the radiator (6504) by an opening distance based on the wavelength of the electromagnetic wave and / or the style of the radiator (6504) or antenna (900). For example, the opening distance, such as the distance between the radiator (6504) and the inner surface (6511), may be at least 1 / 4 of the wavelength of the electromagnetic wave.

[0402] In one embodiment, the electromagnetic absorber (6502) may be positioned adjacent to the hollow waveguide (208). For example, the distal surface (6508) of the electromagnetic absorber (6502) may have a diameter a that defines the cross-sectional dimensions. The distal surface (6508) may be in contact with the hollow waveguide (208). In other embodiments, the electromagnetic absorber (6502) may be positioned to be in contact with the hollow waveguide (208), for example, in contact with or in a state of contact with it. In yet another embodiment, the electromagnetic absorber (6502) may have a peripheral surface (6512) positioned within the hollow waveguide (208) and adjacent to or in a state of contact with the inner surface (312) of the hollow waveguide (208). The diameter a defining the cross-sectional dimension may be within a range of at least 4 to 50 wavelengths of an electromagnetic wave having data encoded within a carrier frequency in the range of 300 GHz to 10 THz, wherein the electromagnetic wave has a predetermined wavelength. In some embodiments, the periphery surface (6512) has a cylindrical shape. However, it should be understood that the periphery surface (6512) may have other shapes, such as a series of adjacent planar sections, to provide a cross-section of a rectangular, hexagonal, or octagonal shape, for example. In some embodiments, the periphery surface (6512) may have a non-uniform or fanciful shape.

[0403] In one embodiment, the electromagnetic absorber (6502) may be composed of an EM absorbing material selected to absorb, attenuate, and / or otherwise limit the reflection of electromagnetic waves (e.g., electromagnetic waves having transmitted signals). In one embodiment, the EM absorbing material may be composed of a porous and / or lossy material. In some embodiments, the EM absorbing material is composed of a semi-porous material having a plurality of randomly located and sized openings having a size of the electromagnetic wave wavelength, i.e., 1 / 100 of the electromagnetic wave wavelength to about 2 times the electromagnetic wave wavelength, preferably about 1 / 4 times the electromagnetic wave wavelength. In some embodiments, the EM absorbing material has a texture similar to steel wool. In some embodiments, as illustrated in FIG. 67 and discussed in detail below, for example, the EM absorbing material may be composed as part of the ground plane (904). In one embodiment, the EM absorbing material may comprise a poorly conductive material (i.e., a material having low electrical conductivity), such as, for example, a carbon material or a carbon-containing compound. In other embodiments, other poorly conductive materials other than carbon may be selected.

[0404] In one embodiment, the EM absorbent material may consist of a foam (e.g., a material having a continuous phase in a solid state). The foam may be, for example, an open-cell foam, a closed-cell foam, or a combination thereof. The foam may be carbon-doped or carbon-loaded, that is, the foam may have a form in which carbon is absorbed or adsorbed and disposed within the foam. In some embodiments, the foam is a polyurethane foam. In one embodiment, the EM absorbent material is a colloidal suspension in which carbon particles are suspended within a continuous phase material.

[0405] Now, referring to FIG. 66, a cross-sectional view of another exemplary embodiment of an electromagnetic absorber (6600) configured according to the present disclosure is shown. As illustrated, the electromagnetic absorber (6600) may be positioned around one or more radiators (6504), such as a first radiator (6504a) and a second radiator (6504b), and may also be positioned within a hollow waveguide (208) (illustrated as a sixth hollow waveguide (208f)). As described in detail above, in some embodiments, the first radiator (6504a) and the second radiator (6504b) may be attached to one or more ground planes (904) as illustrated in FIG. 65. In one embodiment, the electromagnetic absorber (6600) may be configured according to the electromagnetic absorber (6502) described in detail above, for example, of an EM absorbing material.

[0406] In one embodiment, the sixth hollow waveguide (208f) may have an inner surface (312) having a diameter d that defines a cavity (6604) and also defines a cross-sectional dimension. The sixth hollow waveguide (208f) may be configured according to any of the hollow waveguides (208a-n) described in more detail above; however, the sixth hollow waveguide (208f) illustrated in FIG. 66 is exemplified as a hollow core optical fiber cable having a conductive layer (316) surrounding a dielectric layer (308). In other embodiments, the sixth hollow waveguide (208f) may be a metallic, non-optic waveguide.

[0407] The electromagnetic absorber (6600) may have a surrounding surface (6608) in contact with at least a portion of the inner surface (312) of the sixth hollow waveguide (208f), i.e., the hollow core optical fiber cable. In some embodiments, the electromagnetic absorber (6600) has a diameter a that defines a cross-sectional dimension smaller than or equal to the diameter d of the sixth hollow waveguide (208f), so that the electromagnetic absorber (6600) may extend or be fitted into the cavity (6604) of the sixth hollow waveguide (208f) so as not to interfere with the radiators (6504) receiving energy from the electromagnetic waves.

[0408] In one embodiment, the sixth hollow waveguide (208f) further comprises a tapering section (6612) having a first end (6614) and a second end (6616). The first end (6614) may have an inner diameter t and the second end (6616) may have a diameter d, and accordingly, within the tapering section (6612), the diameter of the sixth hollow waveguide (208f) changes from diameter d to inner diameter t. As illustrated, the inner diameter t may be smaller than the diameter d.

[0409] In one embodiment, the electromagnetic absorber (6600) may extend within the sixth hollow waveguide (208f). In some embodiments, the electromagnetic absorber (6600) extends beyond the tapered section (6612) of the sixth hollow waveguide (208f). In other embodiments, the electromagnetic absorber (6600) extends only within the tapered section (6612) of the sixth hollow waveguide (208f). In one embodiment, as illustrated in FIG. 66, the electromagnetic absorber (6600) may extend within the first portion (6620) of the tapered section (6612) of the sixth hollow waveguide (208f).

[0410] In some embodiments, the electromagnetic absorber (6600) in the sixth hollow waveguide (208f) may have a thickness (6622). The thickness (6622) may be uniform within the tapering section (6612), for example, within the first part (6620) of the tapering section (6612). In other embodiments, the electromagnetic absorber (6600) in the sixth hollow waveguide (208f) may have a variable thickness (6622), so that the thickness (6622) gradually decreases from the distal surface (6624) of the electromagnetic absorber (6600) toward the inner end (6626) of the electromagnetic absorber (6600), and may be finished in a feather-edge shape, for example, as exemplified by the tapering absorber surface (6628, shown in dashed line). The tapered absorber surface (6628) can be tapered at different rates from the distal surface (6624) of the electromagnetic absorber (6600) to the inner end (6626).

[0411] Now, referring to FIG. 67, a cross-sectional view of an exemplary embodiment of an electromagnetic absorber (6700) configured according to the present disclosure is shown. As illustrated, the electromagnetic absorber (6700) may be integrated with a fifth ground plane (904e). In this embodiment, the electromagnetic absorber (6700) may include a plurality of vias (6712) having a via diameter (6704) and a depth (6708). The plurality of vias (6712) may extend from a first surface (6714a) of the fifth ground plane (904e) toward a second surface (6714b) by a depth (6708). In some embodiments, the depth (6708) may extend through at least one layer (6716) of the fifth ground plane (904e), such as a first layer (6716a). Although vias (6712) are described as having a via diameter (6704), vias (6712) may have a cross-section of any suitable shape, such as elliptical, square, circular, and similar, or any irregular shape. In such embodiments, the via diameter (6704) may be, for example, a cross-sectional dimension.

[0412] In some embodiments, one or more of the multiple vias (6712) of the electromagnetic absorber (6700) may extend through the first layer (6716a), while others of the multiple vias (6712) may extend through both the first layer (6716a) and the second layer (6716b). As will be understood by a person skilled in the art, some of the vias (6712) may be characterized as blind vias, meaning that the vias (6712) penetrate only the first layer (6716a) and not the second layer (6716b), or as through vias, meaning that the vias (6712) penetrate both the first layer (6716a) and the second layer (6716b).

[0413] In some embodiments, the depth (6708) of the plurality of vias (6712) may be selected based on the wavelength of the electromagnetic wave. For example, the depth (6708) may be about 1 wavelength. In other embodiments, the depth (6708) may be between 1 / 10 and 10 times the wavelength. In some embodiments, the plurality of vias (6712) may extend through a plurality of layers (6716) until reaching the depth (6708), and in some embodiments, they do not extend through all layers (6716). In some embodiments, a first set of multiple vias (6712) may be configured such that the depth (6708) is a first depth, and a second set of multiple vias (6712) may be configured such that the depth (6708) is a second depth different from the first depth, thereby forming multiple semi-porous ground planes having an array of vias (6712) extending between one or more of the semi-porous ground planes. In one embodiment, the first set and the second set of vias (6712) may be randomly placed within the first surface (6714a) of the fifth ground plane (904e). In other embodiments, the first set and the second set may be placed on the fifth ground plane (904e) in a pattern selected to minimize reflection of electromagnetic waves. In some implementations, the depth (6708) of one or more of the plurality of vias (6712) may be randomly selected to have values ​​of about 10% to about 1000% of the wavelength.

[0414] In some embodiments, multiple vias (6712) are separated from each other by a distance (6720). The distance (6720) can be selected based on the wavelength of the electromagnetic wave. For example, the distance (6720) may be about 1 wavelength. In other embodiments, the distance (6720) may be between about 1 / 10 and 1 time the wavelength.

[0415] In one embodiment, each of the plurality of vias (6712) may be defined by a via surface (6724) extending from a first surface (6714a) to a second surface (6714b), which means a through via. In one embodiment, the surface (6724) of the vias (6712) may be composed of a material including, for example, copper, gold, and / or carbon. In some embodiments, one or more vias (6712) may extend through the first surface (6714a) and the second surface (6714b). In some embodiments, the surface (6724) of the vias (6712) may be composed of an electrically conductive material, such as copper or gold, coated with an electrically dissipative material, such as carbon, to help absorb electromagnetic waves. In some implementations, the via surface (6724) may be textured to help absorb electromagnetic waves. In some implementations, the material may be an EM absorbing material (as discussed above).

[0416] In some embodiments, a plurality of vias (6712) may be formed by removing material from the fifth ground plane (904e). For example, during manufacturing, material may be removed from the first surface (6714a) to a depth (6708) to have a via diameter (6704). In other embodiments, a plurality of vias (6712) may be formed by extending protrusions (6726) from the second surface (6714b), such that the protrusions (6726) have a height (6708) equal to the depth of the surface (6724) and are spaced apart from each other by a distance equal to the via diameter (6704).

[0417] In some embodiments, each of the plurality of vias (6712) may have a via diameter (6704) and an opening width (6730). In some embodiments, the via diameter (6704) may be the width of the via closest to the second surface (6714b). The via diameter (6704) may be the same as or different from the opening width (6730). In some embodiments, a first set of the plurality of vias (6712) may be configured such that the via diameter (6704) and the opening width (6730) are the same, a second set of the plurality of vias (6712) may be configured such that the via diameter (6704) is smaller than the opening width (6730), and a third set of the plurality of vias (6712) may be configured such that the via diameter (6704) is larger than the opening width (6730). The vias (6712) of the first, second, and third sets may be randomly placed within the first surface (6714a) of the fifth ground plane (904e). In some embodiments, the via diameter (6704) and aperture width (6730) of one or more of the plurality of vias (6712) may be randomly selected to have values ​​of about 10% to about 110% of the wavelength.

[0418] Now, referring to FIG. 68, a cross-sectional view of an exemplary embodiment of an electromagnetic absorber (6800) configured according to the present disclosure is shown. As illustrated, the electromagnetic absorber (6800) is a spray-on coating configured as a low-band THz electromagnetic absorber. In one embodiment, the electromagnetic absorber (6800) may be composed of materials according to the electromagnetic absorber (6502) described in detail above, such as EM absorbing materials.

[0419] In one embodiment, the spray-on coating may be a carbon-containing polyurethane foam that, when sprayed onto a substrate such as a ground plane (904), adheres to the ground plane (904) and also forms an irregular or non-uniform coating containing carbon particles. The irregular coating may result in a non-uniform coating containing carbon particles (6804) of various sizes, which may have pores or dimples (6808) having cross-sectional dimensions that are roughly sized to the wavelength of the electromagnetic wave (e.g., about 300 μm). The irregular coating may have a thickness (6812) of at least 1 / 4 of the wavelength. In some embodiments, the irregular coating may have a thickness (6812) of about 1 wavelength of the electromagnetic wave to about 10 wavelengths of the electromagnetic wave.

[0420] Now, referring to FIG. 69, an exemplary embodiment of an electromagnetic absorber (6900) constructed according to the present disclosure is illustrated herein. As illustrated, the electromagnetic absorber (6900) may be a fabric (6904) coated with an EM absorbing material such as carbon. The fabric (6904) may be coated, for example, using a spray-on carbon coating that utilizes a binder to allow carbon to adhere to the fabric (6904). In some embodiments, the fabric (6904) may comprise a fabric doped with carbon.

[0421] In one embodiment, the fabric (6904) may be formed from a plurality of strands (6908) (e.g., weft (6908a) and warp (6908b)) coated (or doped) with carbon particles or another poorly conductive EM absorbing material. In some embodiments, the strands (6908) of the fabric (6904) may be carbon-doped before forming the fabric (6904), whereas in other embodiments, the strands (6908) may be doped after the fabric (6904) is formed.

[0422] In some embodiments, the fabric (6904) may be formed of a solid, continuous-phase material that is doped with carbon and has one or more pores (6920) defined by the rest of the fabric (6904) and positioned to penetrate itself. In some embodiments, carbon particles may be sprayed through the pores (6920) of the continuous-phase material.

[0423] Now, referring to FIG. 70, a flowchart of an exemplary implementation of a process (7000) configured according to the present disclosure is illustrated herein. The process (7000) generally comprises: a step of placing an electromagnetic absorber around a radiator of an antenna (step 7004); and a step of coupling a hollow waveguide to the antenna (step 7008).

[0424] In one embodiment, the step of placing an electromagnetic absorber around the radiator of the antenna (step 7004) includes placing an electromagnetic absorber that surrounds the radiator (e.g., any of an electromagnetic absorber (6502), an electromagnetic absorber (6600), an electromagnetic absorber (6700), an electromagnetic absorber (6800), and an electromagnetic absorber (6900). In one embodiment, the electromagnetic absorber does not come into contact with the radiator(s).

[0425] In one implementation, the step of placing electromagnetic absorbers aro...

Claims

Claim 1 A transmitter comprising: a client-side input configured to receive one or more baseband signals having client data; a transmitter circuit configured to receive the one or more baseband signals from the client-side input and generate one or more antenna feed signals based on the one or more baseband signals; and one or more antennas configured to receive the one or more antenna feed signals from the transmitter circuit, generate one or more radiation signals based on the one or more antenna feed signals, and combine the one or more radiation signals within a hollow waveguide—each of the one or more radiation signals being a radiated electromagnetic wave configured for coherent detection and having a frequency within the range of 300 gigahertz (GHz) to 10 terahertz (THz). Claim 2 A transmitter according to claim 1, wherein each of the one or more antennas is one of a differential waveguide probe antenna, a differential tapered antenna, a differential patch antenna, a helix antenna, and a spiral antenna. Claim 3 A transmitter according to claim 1, wherein the one or more baseband signals comprise a plurality of parallel baseband signals and a serial baseband signal, and the transmitter further comprises a serializer configured to receive the plurality of parallel baseband signals and combine the plurality of parallel baseband signals into the serial baseband signal by utilizing at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM), and the client-side input is configured to receive the serial baseband signal, and the transmitter circuit is configured to receive the serial baseband signal from the client-side input and generate the one or more antenna feed signals based on the serial baseband signal. Claim 4 A transmitter according to claim 1, wherein the one or more baseband signals include a plurality of parallel baseband signals and a serial baseband signal, and the transmitter further includes a deserializer configured to receive the serial baseband signal and divide the serial baseband signal into the plurality of parallel baseband signals by utilizing at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM), and the client-side input is configured to receive the plurality of parallel baseband signals, and the transmitter circuit is configured to receive the plurality of parallel baseband signals from the client-side input and generate the one or more antenna feed signals based on the plurality of parallel baseband signals. Claim 5 A transmitter according to claim 1, wherein the frequency of the one or more radiated signals is a transmission frequency, and the transmitter circuit comprises: one or more local oscillators configured to generate one or more carrier signals—each of the one or more carrier signals having a baseband frequency lower than the transmission frequency—; one or more modulation circuits configured to receive the one or more baseband signals from the client-side input and the one or more carrier signals from the one or more local oscillators and modulate the one or more baseband signals onto the one or more carrier signals to generate one or more modulation signals; and one or more up-converting circuits configured to receive the one or more modulation signals from the one or more modulation circuits and up-convert the one or more modulation signals to generate one or more antenna feed signals—each of the one or more antenna feed signals having the transmission frequency. Claim 6 A receiver comprising: one or more antennas configured to coherently detect one or more radiated signals received from a hollow waveguide and to generate one or more antenna output signals based on said one or more radiated signals, wherein each of said one or more radiated signals is a radiated electromagnetic wave configured for coherent detection and has a frequency within the range of 300 GHz to 10 THz and has client data; a receiver circuit configured to receive said one or more antenna output signals from said one or more antennas and to generate one or more baseband signals based on said one or more antenna output signals; and a client-side output configured to receive said one or more baseband signals from said receiver circuit and to transmit said one or more baseband signals. Claim 7 A receiver according to claim 6, wherein each of the one or more antennas is one of a differential waveguide probe antenna, a differential tapered antenna, a differential patch antenna, a helix antenna, and a spiral antenna. Claim 8 A receiver according to claim 6, wherein the one or more baseband signals comprise a plurality of parallel baseband signals and serial baseband signals, the receiver circuit is configured to generate the serial baseband signal based on the one or more antenna output signals, the client-side output is configured to receive the serial baseband signal from the receiver circuit and transmit the serial baseband signal, and the receiver further comprises a deserializer configured to receive the serial baseband signal and divide the serial baseband signal into the plurality of parallel baseband signals by utilizing at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM). Claim 9 A receiver according to claim 6, wherein the one or more baseband signals include a plurality of parallel baseband signals and a serial baseband signal, the receiver circuit is configured to generate the plurality of parallel baseband signals based on the one or more antenna output signals, the client-side output is configured to receive the plurality of parallel baseband signals from the receiver circuit and transmit the plurality of parallel baseband signals, and the receiver further includes a serializer configured to receive the plurality of parallel baseband signals and combine the plurality of parallel baseband signals to become the serial baseband signal by utilizing at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM). Claim 10 In claim 6, the frequency of the one or more radiated signals is a transmission frequency, and the receiver circuit comprises: one or more local oscillators configured to generate one or more reference signals, wherein each of the one or more reference signals has a baseband frequency lower than the transmission frequency; one or more down-conversion circuits configured to generate one or more modulation signals by receiving the one or more antenna output signals from the one or more antennas and the one or more reference signals from the one or more local oscillators and down-converting the one or more antenna output signals using the one or more reference signals, wherein each of the one or more modulation signals has the baseband frequency; and one or more demodulation circuits configured to receive the one or more modulation signals from the one or more down-conversion circuits and demodulate the one or more modulation signals to generate the one or more baseband signals. Claim 11 As a transceiver: a transmitter; and a receiver, the transmitter is: A client-side input configured to receive one or more first baseband signals having first client data; A transmitter circuit configured to receive one or more first baseband signals from the above client-side input and to generate one or more antenna feed signals based on the one or more first baseband signals; and One or more first antennas configured to receive one or more antenna feed signals from the transmitter circuit, generate one or more first radiation signals based on the one or more antenna feed signals, and couple the one or more first radiation signals into a first hollow waveguide—each of the one or more first radiation signals is a radiated electromagnetic wave configured for coherent detection and has a first frequency within the range of 300 GHz to 10 THz—and the receiver comprises: One or more second antennas configured to coherently detect one or more second radiation signals received from one of the first hollow waveguide and the second hollow waveguide, and to generate one or more antenna output signals based on the one or more second radiation signals—each of the one or more second radiation signals is a radiated electromagnetic wave configured for coherent detection, has a second frequency within the range of 300 GHz to 10 THz, and has second client data—; A receiver circuit configured to receive one or more antenna output signals from one or more second antennas and to generate one or more second baseband signals based on the one or more antenna output signals; and A transceiver comprising a client-side output configured to receive one or more second baseband signals from the receiver circuit and transmit one or more second baseband signals. Claim 12 In claim 11, a transceiver wherein each of the one or more first antennas and the one or more second antennas is one of a differential waveguide probe antenna, a differential tapered antenna, a differential patch antenna, a helix antenna, and a spiral antenna. Claim 13 In claim 11, the one or more first baseband signals comprise a plurality of first parallel baseband signals and a first serial baseband signal, and the one or more second baseband signals comprise a plurality of second parallel baseband signals and a second serial baseband signal; the transmitter further comprises a serializer configured to receive the plurality of first parallel baseband signals and to combine the plurality of first parallel baseband signals into the first serial baseband signal by utilizing at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM); the client-side input is configured to receive the first serial baseband signal; the transmitter circuit is configured to receive the first serial baseband signal from the client-side input and generate the one or more antenna feed signals based on the first serial baseband signal; the receiver circuit is configured to generate the second serial baseband signal based on the one or more antenna output signals; and the client-side output is the receiver A transceiver configured to receive the second serial baseband signal from a circuit and transmit the second serial baseband signal, and further comprising a deserializer configured to receive the second serial baseband signal from the client-side output and to divide the second serial baseband signal into the plurality of second parallel baseband signals by utilizing at least one of PDM, TDM, and WDM. Claim 14 In claim 11, the one or more first baseband signals include a plurality of first parallel baseband signals and a first serial baseband signal, and the one or more second baseband signals include a plurality of second parallel baseband signals and a second serial baseband signal, and the transmitter further includes a deserializer configured to receive the first serial baseband signal and divide the first serial baseband signal into the plurality of first parallel baseband signals by utilizing at least one of polarization division multiplexing (PDM), time division multiplexing (TDM), and wavelength division multiplexing (WDM), and the client-side input is configured to receive the plurality of first parallel baseband signals, and the transmitter circuit is configured to receive the plurality of first parallel baseband signals from the client-side input and generate the one or more antenna feed signals based on the plurality of first parallel baseband signals, and the receiver circuit is configured to generate the plurality of second parallel baseband signals based on the one or more antenna output signals, and the client A transceiver, wherein the side output is configured to receive the plurality of second parallel baseband signals from the receiver circuit and transmit the plurality of second parallel baseband signals, and the receiver further comprises a serializer configured to receive the plurality of second parallel baseband signals and combine the plurality of second parallel baseband signals to become the second serial baseband signal by utilizing at least one of PDM, TDM, and WDM. Claim 15 In paragraph 11, the first frequency of the one or more first radiation signals is a transmission frequency, and the transmitter circuit is: One or more first local oscillators configured to generate one or more carrier signals - each of the one or more carrier signals has a first baseband frequency lower than the transmission frequency -; One or more modulation circuits configured to receive one or more first baseband signals from the client-side input and one or more carrier signals from one or more first local oscillators, and to modulate the one or more first baseband signals onto the one or more carrier signals to generate one or more first modulation signals; and One or more up-conversion circuits configured to receive one or more first modulation signals from one or more modulation circuits and up-convert the one or more first modulation signals to generate one or more antenna feed signals—each of the one or more antenna feed signals having the transmission frequency—the receiver circuit comprises: One or more second local oscillators configured to generate one or more reference signals—each of the one or more reference signals having a second baseband frequency lower than the transmission frequency—; One or more down-conversion circuits configured to generate one or more second modulation signals by receiving one or more antenna output signals from one or more second antennas and one or more reference signals from one or more second local oscillators and down-converting the one or more antenna output signals using the one or more reference signals - each of the one or more second modulation signals has the second baseband frequency -; and A transceiver comprising one or more demodulation circuits configured to receive one or more second modulation signals from one or more down-conversion circuits and demodulate the one or more second modulation signals to generate one or more second baseband signals. Claim 16 In claim 1, the one or more baseband signals are a plurality of baseband signals, the one or more antenna feed signals are a plurality of antenna feed signals including a combined antenna feed signal, the one or more radiation signals include a combined radiation signal, the frequency of the one or more radiation signals is a transmission frequency, and the transmitter circuit is: A plurality of local oscillators configured to generate a plurality of carrier signals - each of the plurality of carrier signals has a baseband frequency lower than the transmission frequency -; A plurality of modulation circuits configured to receive a plurality of baseband signals from the above client-side input and a plurality of carrier signals from the above plurality of local oscillators, and to modulate the plurality of baseband signals onto the plurality of carrier signals to generate a plurality of modulated signals; A plurality of up-conversion circuits configured to receive a plurality of modulation signals from the plurality of modulation circuits and up-convert the plurality of modulation signals to generate a plurality of up-converted signals; and A transmitter comprising: a combiner configured to receive a plurality of up-converted signals from the plurality of up-converted circuits and combine the plurality of up-converted signals to become a combined antenna feed signal; wherein the one or more antennas are configured to receive the combined antenna feed signal from the combiner, generate the combined radiation signal based on the combined antenna feed signal, and combine the combined radiation signal within the hollow waveguide. Claim 17 A transmitter according to claim 16, wherein the combination of the plurality of up-converted signals to become the combined antenna feed signal utilizes at least one of TDM (time division multiplexing) and WDM (wavelength division multiplexing). Claim 18 In claim 6, the one or more baseband signals are a plurality of baseband signals, the one or more antenna output signals are a plurality of antenna output signals including a combined antenna output signal, the one or more radiation signals include a combined radiation signal, the frequency of the one or more radiation signals is a transmission frequency, and the one or more antennas are configured to detect the combined radiation signal received from the hollow waveguide and to generate the combined antenna output signal based on the combined radiation signal, and the receiver circuit is: A splitter configured to receive the combined antenna output signal from the one or more antennas and to divide the combined antenna output signal into the plurality of antenna output signals; A plurality of local oscillators configured to generate a plurality of reference signals - each of the plurality of reference signals has a baseband frequency lower than the transmission frequency -; A plurality of down-conversion circuits configured to generate a plurality of modulation signals by receiving the plurality of antenna output signals from the splitter and the plurality of reference signals from the plurality of local oscillators, and down-converting the plurality of antenna output signals using the plurality of reference signals - each of the plurality of modulation signals has the baseband frequency -; and A receiver comprising a plurality of demodulation circuits configured to receive a plurality of modulation signals from the plurality of down-conversion circuits and demodulate the plurality of modulation signals to generate the plurality of baseband signals. Claim 19 A receiver according to claim 18, wherein the division of the combined antenna output signal into the plurality of antenna output signals utilizes at least one of TDM (time division multiplexing) and WDM (wavelength division multiplexing). Claim 20 In paragraph 11, the one or more first baseband signals are a plurality of first baseband signals, the one or more antenna feed signals are a plurality of antenna feed signals including a combined antenna feed signal, the one or more first radiation signals include a first combined radiation signal, the first frequency of the one or more first radiation signals is a transmission frequency, and the transmitter circuit is: A plurality of local oscillators configured to generate a plurality of carrier signals - each of the plurality of carrier signals has a baseband frequency lower than the transmission frequency -; A plurality of modulation circuits configured to receive a plurality of first baseband signals from the above client-side input and a plurality of carrier signals from the above plurality of local oscillators, and to modulate the plurality of first baseband signals onto the plurality of carrier signals to generate a plurality of modulated signals; A plurality of up-conversion circuits configured to receive a plurality of modulation signals from the plurality of modulation circuits and up-convert the plurality of modulation signals to generate a plurality of up-converted signals; and A transceiver comprising: a combinationr configured to receive a plurality of up-converted signals from the plurality of up-converted circuits and to combine the plurality of up-converted signals to become a combined antenna feed signal; wherein one or more first antennas are configured to receive the combined antenna feed signal from the combinationr, generate a first combined radiation signal based on the combined antenna feed signal, and combine the first combined radiation signal into the first hollow waveguide. Claim 21 In paragraph 20, a transceiver that combines the plurality of up-converted signals to become the combined antenna feed signal, utilizing at least one of TDM (time division multiplexing) and WDM (wavelength division multiplexing). Claim 22 In paragraph 20, the one or more second baseband signals are a plurality of second baseband signals, the one or more antenna output signals are a plurality of antenna output signals including a combined antenna output signal, the one or more second radiation signals include a second combined radiation signal, the second frequency of the one or more second radiation signals is a transmission frequency, and the one or more second antennas are configured to detect the second combined radiation signal received from one of the first hollow waveguide and the second hollow waveguide and to generate the combined antenna output signal based on the second combined radiation signal, and the receiver circuit is: A splitter configured to receive the combined antenna output signal from the one or more second antennas and to divide the combined antenna output signal into the plurality of antenna output signals; A plurality of local oscillators configured to generate a plurality of reference signals - each of the plurality of reference signals has a baseband frequency lower than the transmission frequency -; A plurality of down-conversion circuits configured to generate a plurality of modulation signals by receiving the plurality of antenna output signals from the splitter and the plurality of reference signals from the plurality of local oscillators, and down-converting the plurality of antenna output signals using the plurality of reference signals - each of the plurality of modulation signals has the baseband frequency -; and A transceiver comprising a plurality of demodulation circuits configured to receive a plurality of modulation signals from the plurality of down-conversion circuits and demodulate the plurality of modulation signals to generate the plurality of second baseband signals. Claim 23 In paragraph 22, a transceiver that divides the combined antenna output signal into the plurality of antenna output signals using at least one of TDM (time division multiplexing) and WDM (wavelength division multiplexing).

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