Series compensation control method and control system for dual-active bridge converter

Abstract

The invention discloses a series compensation control method and control system for a dual-active bridge converter, and belongs to the technical field of direct current converter control, and the series compensation control method comprises the steps: determining a current working mode corresponding to a kth beat, calculating a series compensation coefficient of the kth beat in the current working mode by using the voltage transmission ratio of the kth beat, the actual battery current, the control phase shift angle of the previous beat and the duty ratio of the input bus side of the previous beat, and inputting a middle phase shift angle of the kth beat into a series compensation link of the kth beat to obtain a control phase shift angle of the kth beat, and finally, generating a kth-beat driving signal by using the kth-beat control phase shift angle and the kth-beat input bus side duty ratio so as to drive a power switch device of the dual-active bridge converter. The series compensation link can dynamically adjust and expand the working characteristics of the phase-shifted dual-active bridge converter under different working conditions, so that the defect of poor dynamic adaptive capacity of a traditional PI control surface to a wide load range can be overcome.

Description

Technical Field

[0001] The present invention belongs to the technical field of direct current converter control, and more particularly, relates to a series compensation control method and control system for a dual active bridge converter. Background Art

[0002] With the deepening implementation of the "Dual Carbon" strategy, renewable energy consumption technologies, centered around battery energy storage, have become a key enabler for building a new power system. With the introduction of electric vehicle grid integration, electric vehicles are no longer limited to traditional power loads; they will also serve as distributed energy storage units for energy scheduling. In recent years, with the rapid growth of electric vehicle ownership, the application of dual active bridge converters in battery energy management systems has become increasingly widespread.

[0003] The dual active bridge converter occupies an important position in the battery energy management system due to its advantages such as bidirectional power flow capability, natural electrical isolation characteristics and fast charge and discharge switching. The modulation methods of this converter mainly include single phase shift, extended phase shift, double phase shift and triple phase shift. The dual active bridge converter using traditional single phase shift modulation is simple to control, but the circulating power is large during operation, the turn-off current stress of the switching device is high, and it is difficult to achieve soft switching under light load, which limits the further improvement of the system power. To solve such problems, scholars have proposed modulation strategies such as extended phase shift, double phase shift and triple phase shift. They can significantly broaden the soft switching range and suppress the circulating power by introducing additional control degrees of freedom, and are widely used in high-voltage and high-power occasions. Among these modulation strategies, extended phase shift modulation adjusts the phase shift angle D p and the additional duty cycle D on the high side y , while achieving soft switching under full-load conditions and significantly suppressing circulating current, the dual-active-bridge converter improves efficiency over a wide load range, achieving an optimal balance between algorithm complexity and performance. However, the multiple operating modes introduced by the extended phase-shift modulation method and the wide range of battery operating conditions present significant challenges to the control system of the dual-active-bridge converter.

[0004] In high-power charging and discharging applications, battery loads place high demands on the converter's dynamic performance. For example, when current commands switch between positive and negative in vehicle-grid interaction and energy storage peak-shaving applications, the converter must be able to respond quickly and with zero overshoot. Even slight overshoot or delay can cause system component failure. A fast and smooth current response not only reduces electrical and thermal stress but also significantly improves system reliability. Furthermore, excellent dynamic performance enables precise current waveform control under extreme operating conditions, thereby optimizing battery health and extending battery life.

[0005] As the range of connected battery voltages continues to expand, extended phase-shifted dual active bridge converters (EPDBCs) face significant challenges in coping with wide variations in current commands. Currently, the control method for EPDBCs is primarily PI control. As the battery load conditions change, the operating characteristics of the EPDBCs change accordingly. Under traditional PI control, EPDBCs suffer from slow dynamic response due to the wide range of connected battery voltage and current variations. Under certain operating conditions, the system may even experience system instability and oscillation, becoming unable to maintain normal operation. Summary of the Invention

[0006] In response to the above-mentioned defects or improvement needs of the prior art, the present invention provides a series compensation control method and control system for a dual active bridge converter, the purpose of which is to solve the technical problems of slow dynamic response speed and poor stability of the extended phase-shifted dual active bridge converter under the traditional PI control method in battery charging and discharging application scenarios.

[0007] To achieve the above object, according to one aspect of the present invention, a series compensation control method for a dual active bridge converter is provided, comprising: performing the following steps at the kth beat:

[0008] Collect the input bus voltage V of the kth beat in (k), the battery bus voltage V at the kth beat b (k) and the actual battery current I at the kth beat b (k);

[0009] Using the k-th beat input bus voltage V in (k), the battery bus voltage V of the kth beat b (k) and the input transformer ratio N to calculate the voltage transfer ratio m(k) of the kth beat;

[0010] The reference current instruction I ref and the actual battery current I of the kth beat b The difference e of (k) i (k) Input current controller G c Get the intermediate phase shift angle D of the kth beat p_0 (k);

[0011] Determine the current working mode corresponding to the kth beat, and use the voltage transfer ratio m(k) of the kth beat and the actual battery current I of the kth beat b (k) The control phase shift angle D of the previous beat p (k-1) and the input bus duty cycle D of the previous beat y (k-1) Calculate the series compensation coefficient G of the kth beat in the current working mode s (k);

[0012] The middle phase shift angle D of the kth beat p_0 (k) Input the series compensation coefficient G of the kth beat s (k) The corresponding series compensation link obtains the control phase shift angle D of the kth beat p (k);

[0013] The voltage transfer ratio m(k) of the kth beat and the control phase shift angle D of the kth beat are used. p (k) Determine the duty cycle D of the input bus side at the kth beat y (k);

[0014] The control phase shift angle D of the kth beat is used p (k) and the input bus side duty cycle D of the kth beat y (k) Generate a k-th beat driving signal to drive the power switching device of the dual active bridge converter.

[0015] Furthermore, the voltage transfer ratio m(k) of the kth beat and the actual battery current I of the kth beat are used. b (k) The control phase shift angle D of the previous beat p (k-1) and the input bus duty cycle D of the previous beat y (k-1) Calculate the series compensation coefficient G of the kth beat in the current working mode s (k), including: when the current working mode is working mode 1, the series compensation coefficient G is calculated using the following formula s (k):

[0016]

[0017] Furthermore, the voltage transfer ratio m(k) of the kth beat and the actual battery current I of the kth beat are used. b (k) The control phase shift angle D of the previous beat p (k-1) and the input bus duty cycle D of the previous beat y (k-1) Calculate the series compensation coefficient G of the kth beat in the current working mode s (k), including: when the current working mode is working mode 2, the series compensation coefficient G is calculated using the following formula s (k):

[0018]

[0019] Furthermore, determining the current working mode corresponding to the k-th beat includes: when the following conditions are met, the current working mode is considered to be the working mode 1, otherwise it is considered to be the working mode 2:

[0020]

[0021] Furthermore, the voltage transfer ratio m(k) of the kth beat and the control phase shift angle D of the kth beat are used. p (k) Determine the duty cycle D of the input bus side at the kth beat y (k), including: using the following formula to determine the input bus side duty cycle D of the kth beat y (k);

[0022]

[0023] Furthermore, the intermediate phase shift angle D of the k-th beat is p_0 (k) Input the series compensation coefficient G of the kth beat s (k) The corresponding series compensation link obtains the control phase shift angle D of the kth beat p (k), comprising: shifting the intermediate phase angle D of the k-th beat p_0 (k) Input the series compensation coefficient G of the kth beat s (k) The corresponding series compensation link obtains the control phase shift angle D of the kth beat p (k), D p (k) = D p_0 (k)G s (k).

[0024] Furthermore, the reference current instruction I ref and the actual battery current I of the kth beat b The difference e of (k) i (k) Input current controller G c Get the intermediate phase shift angle D of the kth beat p_0 (k), including: using the following formula to determine the intermediate phase shift angle D of the kth beat p_0 (k):

[0025] D p_0 (k) = D p_0 (k-1)+K p [e i (k)-e i (k-1)]+T s K i e i (k)

[0026] Among them, D p_0 (k-1) is the middle phase shift angle of the k-1th beat, e i (k-1) is the error of the k-1th beat, K p is the proportionality coefficient, K i is the integral coefficient, T s is the calculation period of the k-th beat.

[0027] Furthermore, the control phase shift angle D of the kth beat is used p (k) and the input bus side duty cycle D of the kth beat y (k) generating a driving signal of the kth beat to drive the power switch device of the dual active bridge converter, including: shifting the control phase angle D of the kth beat to p (k) and the input bus side duty cycle D of the kth beat y (k) generating a k-th beat drive signal g1-g8 for the dual active bridge converter switch tubes Q1-Q8 via a DPWM module; the k-th beat drive signal g1-g8 is used to control the switch tubes Q1-Q8 to be turned on and off according to a preset rule, dynamically suppressing the k-th beat battery bus voltage V b (k) and the actual battery current I of the kth beat b (k) Impact on the control system to improve the dynamic performance of the dual active bridge converter under a wide load range.

[0028] According to another aspect of the present invention, a control system for a dual active bridge converter is provided, comprising a memory and a processor, wherein the memory stores a computer program, and the processor implements the steps of the series compensation control method for the dual active bridge converter when executing the computer program.

[0029] According to another aspect of the present invention, a computer-readable storage medium is provided, on which a computer program is stored. When the computer program is executed by a processor, the steps of the series compensation control method of the dual active bridge converter are implemented.

[0030] In general, the above technical solutions conceived by the present invention can achieve the following beneficial effects compared with the prior art:

[0031] (1) The present invention provides a series compensation control method for a dual active bridge converter, which inputs physical quantity information such as battery voltage and current into the series compensation link, and calculates and updates the series compensation link G in real time through an iterative algorithm. s This series compensation link dynamically adjusts the operating characteristics of the extended phase-shifted dual-active bridge converter under different operating conditions, thereby accommodating changes in operating characteristics introduced by wide fluctuations in the connected battery voltage and current, significantly improving the dynamic performance of the extended phase-shifted dual-active bridge converter over a wide load range. This method can overcome the shortcomings of traditional PI control in its poor dynamic adaptability to a wide load range.

[0032] (2) This scheme inputs the previous calculation amount and the real-time collected battery voltage and current information into the series compensation link, and adjusts the series compensation coefficient online through simple calculation. This series compensation control method is combined with PI control to achieve fast dynamic response of the converter under full load conditions. In addition, the calculation of this method does not involve information on key converter parameters such as inductance and frequency, which makes it easy to expand to various power level application scenarios, with stronger robustness and wider applicability.

[0033] (3) This plan should meet the following requirements: When , the current working mode is regarded as the working mode 1, otherwise it is the working mode 2; this judgment method is simple, has low computational complexity, and can improve the execution efficiency of the entire control algorithm.

[0034] (4) This solution shifts the intermediate phase angle D of the kth beat p_0 (k) Input the series compensation coefficient G of the kth beat s (k) The corresponding series compensation link obtains the control phase shift angle D of the kth beat p (k), D p (k) = D p_0 (k)G s (k) The control algorithm is simple and does not require any extra hardware circuits. BRIEF DESCRIPTION OF THE DRAWINGS

[0035] Figure 1 1 is a schematic structural diagram of an extended phase-shifted dual active bridge converter according to an embodiment of the present invention;

[0036] Figure 2 This is a flow chart of a series compensation control method for improving the dynamic performance of a dual active bridge converter over a wide load range in one embodiment of the present invention;

[0037] Figure 3 is a flow chart of a series compensation control method for improving the dynamic performance of a dual active bridge converter over a wide load range in another embodiment of the present invention;

[0038] Figure 4 This is a block diagram of the series compensation control system of the extended phase-shifted dual active bridge converter;

[0039] Figure 5a 、 5b and 5c are the battery voltage V in one embodiment of the present invention. b =450V, V b =250V, V b =100V experimental waveform. DETAILED DESCRIPTION

[0040] In order to make the objectives, technical solutions and advantages of the present invention more clearly understood, the present invention is further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are merely for the purpose of explaining the present invention and are not intended to limit the present invention. In addition, the technical features involved in the various embodiments of the present invention described below may be combined with each other as long as they do not conflict with each other.

[0041] Figure 1 The battery charging and discharging system structure diagram based on extended phase-shifted dual active bridge converter, 1 is the input voltage V in Bidirectional DC source, 2 is the main circuit part of the extended phase-shifted dual active bridge converter, including input filter capacitor C1, the first H-bridge circuit Q1-Q4, and the series resonant inductor L r , high frequency transformer T r , the second H-bridge circuit Q5-Q8, the output filter capacitor C f . Among them, the high frequency transformer T r The transformation ratio is N:1. 3 is the power battery pack, 4 is the control system circuit, mainly including the input voltage V in , battery voltage V b and battery current I b Sampling calculation module, PI control module G c , dynamic series compensation link G s And DPWM drive generation module. When the system is running, the collected bus voltage V in Battery voltage V b and battery current I b The physical quantity is input into the proposed series compensation control algorithm to dynamically generate the control phase shift angle D of the extended phase-shifted dual active bridge converter. p and duty cycle D y The DPWM module outputs the corresponding drive signals g1-g8 to achieve the battery charge and discharge current I b For current command I ref Fast follow.

[0042] As the battery voltage and current commands change over a wide range, the series compensation link G s Based on these changes, dynamic series compensation correction is performed according to certain rules, so that the control system can absorb the changes in the working characteristics of the dual active bridge converter caused by changes in load conditions and achieve rapid dynamic response under full load conditions.

[0043] In this embodiment, the input bus voltage V in =700V, connected to the battery voltage V bThe voltage range is 100-450V, the rated charge and discharge current is ±100A, and the operating frequency of the switching devices Q1-Q8 is 10kHz. The main power topology parameters include transformer ratio N=3:2, series inductor L r =45μH, input power side filter capacitor C1 = 1000μF, output battery side filter capacitor C f =2000μF.

[0044] like Figure 2 As shown, the present invention provides a series compensation control method for a dual active bridge converter, which can improve the dynamic performance of the dual active bridge converter in a wide load range, including the following steps.

[0045] S1: Collect the current input bus voltage V in (k) Current battery bus voltage V b (k) and the actual battery current I b (k); Using the current input bus voltage V in (k) Current battery bus voltage V b (k) and the input transformer ratio N are used to calculate the voltage transfer ratio m(k) of the current beat. In one embodiment, the expression of the voltage transfer ratio m(k) of S1 is:

[0046]

[0047] Wherein, N is the transformation ratio of the high frequency transformer.

[0048] S2: Set the reference current instruction I ref and the actual battery current I b The difference e of (k) i (k) Input current controller G c Get the intermediate phase shift angle D of the current beat p_0 (k). Specifically, S3 current controller G c for:

[0049]

[0050] Among them, K p is the proportionality coefficient, K i is the integral coefficient. The current error signal e i (k) Get the intermediate phase shift angle D p_0 The calculation process of (k) is as follows:

[0051] D p_0 (k) = D p_0 (k-1)+K p [e i (k)-e i(k-1)]+T s K i e i (k)

[0052] Among them, T s is the calculation period of the control beat. p_0 (k-1) is the middle phase shift angle of the k-1th beat, e i (k-1) is the error of the k-1th beat, K p is the proportionality coefficient, K i is the integral coefficient, T s is the calculation period of the k-th beat.

[0053] S3: Determine the current working mode corresponding to the current beat, using the voltage transfer ratio m(k) of the current beat and the actual battery current I b (k) The control phase shift angle D of the previous beat p (k-1) and the input bus duty cycle D of the previous beat y (k-1) Calculate the series compensation coefficient G of the current beat in the current working mode s (k).

[0054] Specifically, the phase shift angle D is controlled by the previous beat p (k-1) and the voltage transfer ratio m(k-1) to determine the working mode of the converter, and according to the working mode, battery voltage V b (k) and current I b (k) Get the corresponding series compensation link G s (k);

[0055]

[0056] S4: Shift the middle phase angle of the current shot by D p_0 (k) Input the series compensation coefficient G of the current beat s (k) The corresponding series compensation link obtains the control phase shift angle D of the current beat p (k); using the voltage transfer ratio m(k) of the current beat and the control phase shift angle D of the current beat p (k) Determine the input bus side duty cycle D of the current beat y (k). Specifically, the intermediate phase shift angle D p_0 (k) Input series compensation link G s (k) Get the final control phase shift angle D p (k), D p (k) = D p_0 (k)G s (k), and according to the working mode and control phase shift angle D p (k) Determine the corresponding input bus side duty cycle Dy (k);

[0057]

[0058] S5: Use the current beat to control the phase shift angle D p (k) and the current input bus side duty cycle D y (k) Generate a driving signal for the current beat to drive the power switch device of the dual active bridge converter and enter the loop calculation for the next beat to control the battery current I b .

[0059] Figure 3 FIG. 4 is an algorithm flow chart of a series compensation control method for a dual active bridge converter in another embodiment of the present invention.

[0060] First, enter the ADC interrupt and detect the current input bus voltage V in (k), battery bus side voltage V b (k) and the actual current I on the battery bus b (k), and based on the real-time acquisition of the current voltage signal V in (k) and V b (k) and the input transformer ratio N are used to calculate the voltage transfer ratio m(k) of the converter. ref and the collected battery current I b (k) Take the difference to get the current error signal e i (k), and the current error signal e i (k) Input current controller G c Get the intermediate phase shift angle D p_0 (k) Control the phase shift angle D according to the upbeat result p The relationship between (k-1) and the voltage transfer ratio m(k-1) determines the working mode of the converter, that is, D p (k-1)≤[1-m(k-1)] / 2, it is working mode 1, otherwise it is working mode 2. The series compensation link G is calculated according to the corresponding working mode. s (k); shift the intermediate phase angle D p_0 (k) Through the series compensation link G s (k) Get the final control phase shift angle D p (k), and output the corresponding bus V according to the converter working mode in Duty cycle D y (k). Control the phase shift angle D p (k) and duty cycle D y (k) is input to the DPWM module to generate the driving signal of the k-control switching device and enters the k+1 beat cycle calculation to control the battery current I b.

[0061] Figure 4 This is the specific control block diagram of the series compensation control method. Figure 4 It can be seen that because the series compensation link G s The existence of can dynamically adjust the operating characteristics of the dual active bridge converter, so that the current controller can maintain excellent dynamic performance under full load conditions.

[0062] Finally, a 50kW extended phase-shifted dual active bridge converter prototype was built in the laboratory with the parameters as shown in the example above. b =450V, the series compensation control method is evaluated at the battery current reference value I ref Dynamic performance during continuous step changes. Experimental test results are as follows Figure 5a , specifically including the voltage v at the two H-bridge AC points AB and v CD , series inductor L r The current i Lr , battery voltage V b And the battery charge and discharge current I b .Depend on Figure 5a It can be seen that the I set at five different times ref The battery current jumps from 0A to 50A, 50A to 100A, 100A to -100A, -100A to -50A, and -50A back to 0A. b Tracks I without overshoot in all step commands ref The regulation times were 2.1ms, 2.1ms, 3.3ms, 2.1ms, and 2.0ms, respectively. The extreme operating response time for a full-load power conversion from 100A to -100A was only 3.3ms. This test fully demonstrated the series compensation scheme's robustness to extreme transient conditions. Figure 5b is the battery voltage V b =250V experimental results. Figure 5b It can be seen that the experimental data show that i b Tracks I without overshoot in all step commands ref The adjustment times are 2.1ms, 2.1ms, 5.2ms, 2.2ms and 2.1ms respectively. Figure 5c is the battery voltage V b =100V experimental results. Figure 5b It can be seen that I b Tracks I without overshoot in all step commands ref, and their adjustment times are 2.4ms, 2.4ms, 4.5ms, 2.4ms, and 2.4ms, respectively. In summary, the proposed series compensation control method can significantly improve the dynamic response performance of the extended phase-shifted dual active bridge converter under a wide range of battery voltage conditions of 100-450V. And under the most extreme conditions, that is, V b =100V, when the current command switches from 100A to -100A, the response time is only 4.5ms.

[0063] Example 2

[0064] This embodiment provides a control system for a dual active bridge converter, including a memory and a processor. The memory stores a computer program, and the processor implements the steps of a series compensation control method for the dual active bridge converter when executing the computer program.

[0065] Example 3

[0066] This embodiment provides a computer-readable storage medium having a computer program stored thereon. When the computer program is executed by a processor, the steps of the series compensation control method of the dual active bridge converter are implemented.

[0067] It will be easily understood by those skilled in the art that the above description is merely a preferred embodiment of the present invention and is not intended to limit the present invention. Any modifications, equivalent substitutions, and improvements made within the spirit and principles of the present invention should be included in the scope of protection of the present invention.

Claims

1. A series compensation control method for a dual active bridge converter, characterized in that: include: At the kth beat, perform the following steps: Collect the input bus voltage V of the kth beat in (k), the battery bus voltage V at the kth beat b (k) and the actual battery current I at the kth beat b (k); Using the k-th beat input bus voltage V in (k), the battery bus voltage V of the kth beat b (k) and the input transformer ratio N to calculate the voltage transfer ratio m(k) of the kth beat; The reference current instruction I ref and the actual battery current I of the kth beat b The difference e of (k) i (k) Input current controller G c Get the intermediate phase shift angle D of the kth beat p_0 (k); Determine the current working mode corresponding to the kth beat, and use the voltage transfer ratio m(k) of the kth beat and the actual battery current I of the kth beat b (k) The control phase shift angle D of the previous beat p (k-1) and the input bus duty cycle D of the previous beat y (k-1) Calculate the series compensation coefficient G of the kth beat in the current working mode s (k); The middle phase shift angle D of the kth beat p_0 (k) Input the series compensation coefficient G of the kth beat s (k) The corresponding series compensation link obtains the control phase shift angle D of the kth beat p (k); The voltage transfer ratio m(k) of the kth beat and the control phase shift angle D of the kth beat are used. p (k) Determine the duty cycle D of the input bus side at the kth beat y (k); The control phase shift angle D of the kth beat is used p (k) and the input bus side duty cycle D of the kth beat y (k) Generate a k-th beat driving signal to drive the power switching device of the dual active bridge converter.

2. The series compensation control method for a dual active bridge converter according to claim 1, wherein: The voltage transfer ratio m(k) of the k-th beat and the actual battery current I of the k-th beat are used. b (k) The control phase shift angle D of the previous beat p (k-1) and the input bus duty cycle D of the previous beat y (k-1) Calculate the series compensation coefficient G of the kth beat in the current working mode s (k), including: When the current working mode is working mode 1, the series compensation coefficient G is calculated using the following formula: s (k):

3. The series compensation control method for a dual active bridge converter according to claim 1, wherein: The voltage transfer ratio m(k) of the k-th beat and the actual battery current I of the k-th beat are used. b (k) The control phase shift angle D of the previous beat p (k-1) and the input bus duty cycle D of the previous beat y (k-1) Calculate the series compensation coefficient G of the kth beat in the current working mode s (k), including: When the current working mode is working mode 2, the series compensation coefficient G is calculated using the following formula: s (k):

4. The series compensation control method for a dual active bridge converter according to claim 2 or 3, wherein: The determining of the current working mode corresponding to the k-th beat includes: when the following conditions are met, the current working mode is considered to be the working mode 1; otherwise, the current working mode is considered to be the working mode 2:

5. The series compensation control method for a dual active bridge converter according to claim 4, wherein: The voltage transfer ratio m(k) of the k-th beat and the control phase shift angle D of the k-th beat are used. p (k) Determine the duty cycle D of the input bus side at the kth beat y (k), including: using the following formula to determine the input bus side duty cycle D of the kth beat y (k); 6. The series compensation control method for a dual active bridge converter according to claim 1, wherein: The intermediate phase shift angle D of the k-th beat is p_0 (k) Input the series compensation coefficient G of the kth beat s (k) The corresponding series compensation link obtains the control phase shift angle D of the kth beat p (k), including: The middle phase shift angle D of the kth beat p_0 (k) Input the series compensation coefficient G of the kth beat s (k) The corresponding series compensation link obtains the control phase shift angle D of the kth beat p (k), D p (k) = D p_0 (k)G s (k).

7. The series compensation control method for a dual active bridge converter according to claim 6, wherein: The reference current instruction I ref and the actual battery current I of the kth beat b The difference e of (k) i (k) Input current controller G c Get the intermediate phase shift angle D of the kth beat p_0 (k), including: using the following formula to determine the intermediate phase shift angle D of the kth beat p_0 (k): D p_0 (k)=D p_0 (k-1)+K p [e i (k)-e i (k-1)]+T s K i e i (k) Among them, D p_0 (k-1) is the middle phase shift angle of the k-1th beat, e i (k-1) is the error of the k-1th beat, K p is the proportionality coefficient, K i is the integral coefficient, T s is the calculation period of the k-th beat.

8. The series compensation control method for a dual active bridge converter according to claim 1, wherein: The control phase shift angle D of the k-th beat is used p (k) and the input bus side duty cycle D of the kth beat y (k) generating a k-th beat driving signal to drive a power switching device of the dual active bridge converter, comprising: The control phase shift angle D of the kth beat is p (k) and the input bus side duty cycle D of the kth beat y (k) generating a k-th beat drive signal g1-g8 for the dual active bridge converter switch tubes Q1-Q8 via a DPWM module; the k-th beat drive signal g1-g8 is used to control the switch tubes Q1-Q8 to be turned on and off according to a preset rule, dynamically suppressing the k-th beat battery bus voltage V b (k) and the actual battery current I of the kth beat b (k) Impact on the control system to improve the dynamic performance of the dual active bridge converter under a wide load range.

9. A control system for a dual active bridge converter, comprising a memory and a processor, wherein the memory stores a computer program, characterized in that: When the processor executes the computer program, the steps of the method according to any one of claims 1 to 8 are implemented.

10. A computer-readable storage medium having a computer program stored thereon, characterized in that: When the computer program is executed by a processor, the steps of the method according to any one of claims 1 to 8 are implemented.

Images