Multi-output non-right half-plane zero power conversion architecture and related circuits and techniques

Abstract

The invention discloses a multi-output non-right half-plane zero power conversion architecture and related circuits and techniques. Concepts, systems, system architectures, circuits, methods, and techniques are described for power management and control. In particular, concepts, systems, system architectures, circuits, methods, and techniques are described for implementing power converters that may not have right derivative zero poles in their linearized averaged control to output transfer functions, but still may have buck and boost functions.

Description

Technical Field

[0001] The present application relates to power converters, and more particularly to a multi-output non-right half plane zero power conversion architecture and related circuits and techniques. Background Art

[0002] The efficiency of radio frequency (RF) power amplifiers (PAs) can be improved through "supply modulation" (or "drain modulation" or "collector modulation"), in which the supply voltage supplied to the PA is dynamically adjusted ("modulated") over time based on the RF signal being synthesized. For maximum efficiency improvement, the supply voltage can be continuously adjusted between discrete voltage levels or over short timescales to track or dynamically adapt to rapid changes in the RF signal amplitude (or envelope). For example, these rapid changes in the RF signal can occur when data is encoded in the RF signal or when the RF signal amplitude is expected to vary with a high envelope bandwidth (e.g., as in envelope tracking, advanced envelope tracking, polar modulation, "class G" power amplification, multi-stage back-off, multi-stage linear amplifier with nonlinear components (LINC), asymmetric multilevel out-phasing (AMO)). The supply voltage (or voltage level) supplied to the PA can also be adapted to accommodate long-term changes in the expected RF envelope. This is sometimes referred to as "adaptive biasing." For example, such "long term variations" may be associated with adapting transmitter output strength to reduce, and ideally minimize, errors in data transfer, or adapting transmitter output strength to RF "traffic" variations, or the like.

[0003] "Continuous" supply modulation (e.g., "envelope tracking" or "adaptive biasing") can be advantageously implemented by dynamically selecting an intermediate voltage from a set of discrete supply voltages and then further adjusting (e.g., stepping down) the intermediate voltage to produce a continuously variable supply voltage to be provided to the power amplifier. "Continuous" supply modulation is alternatively implemented by pulse-width modulating between two or more voltage levels and filtering the output to produce a continuously varying waveform. Some RF amplifier systems utilize "discrete" supply modulation (or discrete "drain modulation"), in which the supply voltage is switched between a set of discrete voltage levels. Some of these systems include additional filtering or modulation to shape the voltage transitions between the levels. Systems of this type are known and include, for example, "Class G" amplifiers, multi-stage LINC (MLINC) power amplifiers, AMO power amplifiers, multi-stage back-off amplifiers (including "asymmetric multi-stage back-off" amplifiers), and digital polar transmitters.

[0004] It is also possible to implement hybrid systems that utilize a combination of continuous and discrete supply modulation. Summary of the Invention

[0005] This document describes concepts, systems, system architectures, circuits, methods, and techniques for power management. In particular, concepts, systems, system architectures, circuits, methods, and techniques for power management involving power converters (or more simply, "converters") that do not exhibit right-half-plane zeros in their linearized, averaged control-to-output transfer functions, referred to herein as non-right-half-plane-zero (NRHPZ) converters, are described. The concepts, systems, system architectures, circuits, methods, and techniques described herein can be used in a variety of applications, including, but not limited to, mobile handheld applications, as well as many other power management applications.

[0006] In some embodiments, circuits are described that include NRHPZ converters with both buck and boost functionality. For example, these circuits may include a converter having a switched capacitor stage and a magnetic stage. In some embodiments, these circuits may include switches rated for voltages higher than the input voltage from the energy source. In some embodiments, these circuits may include switches rated only for voltages as high as the input voltage from the energy source. In some embodiments, these circuits may incorporate flying capacitors for energy transfer to support voltages higher than the input voltage from the energy source. In some embodiments, these circuits may incorporate interleaved switched capacitor stages and magnetic stages. In some embodiments, these circuits may incorporate magnetic stages and switched capacitor multi-output stages. In some embodiments, these circuits may incorporate magnetic stages and both interleaved switched capacitor stages and switched capacitor multi-output stages.

[0007] In some embodiments, circuits are described that include an NRHPZ converter having buck and boost functionality and a reconfigurable front end. For example, these circuits may include a converter having reconfigurable switched capacitor and magnetic stages. In some embodiments, these circuits may include interleaved reconfigurable switched capacitor and magnetic stages. In some embodiments, these circuits may include a first magnetic-based front end stage and a second magnetic stage. In some embodiments, these circuits may include switches rated for voltages higher than the voltage of the input voltage from an energy source. In some embodiments, these circuits may include switches rated only for voltages as high as the input voltage from an energy source.

[0008] In some embodiments, circuits are described that include NRHPZ converters with buck and boost functionality that do not require a front-end stage. For example, these circuits may include a converter that utilizes flying capacitors to provide a switching voltage level greater than the input voltage of an energy source. In some embodiments, these circuits may utilize interleaved flying capacitor circuits to provide a switching voltage level greater than the input voltage of an energy source.

[0009] In some embodiments, circuits are described that include NRHPZ converters with buck and boost functionality and utilizing a multi-output architecture. For example, these circuits can include a converter utilizing multiple NRHPZ converters, wherein the inputs of the NRHPZ converters are connected to an energy source, and wherein each of the NRHPZ converters has an output connected to the input of a switched-capacitor converter. In some embodiments, these circuits can include multiple NRHPZ converters connected in cascade, wherein each of the NRHPZ converters has an output connected to the input of a switched-capacitor converter. In some embodiments, these circuits can include multiple NRHPZ converters that share a "boost" switched-capacitor front-end stage or a magnetic front-end stage. In some embodiments, these circuits can include multiple NRHPZ converters, each connected to a switched-capacitor multi-output converter. In some embodiments, these circuits can include an NRHPZ converter connected to a switched-capacitor multi-output converter. In some embodiments, these circuits can include both an NRHPZ converter and a switched-capacitor multi-output converter connected to a switched-capacitor front-end.

[0010] In some embodiments, circuits are described that include NRHPZ converters with buck and boost functionality and utilize three-phase operation. In some embodiments, these circuits can switch between two-phase operation and three-phase operation.

[0011] According to some embodiments, a power converter is provided. The power converter has an input terminal pair configured to be connected to opposite terminals of a voltage source, and has an output terminal configured to be coupled to a load. The power converter includes a magnetic stage. The magnetic stage includes a first plurality of switches and an inductor. The power converter also includes an output stage coupled to the magnetic stage. The output stage includes a second plurality of switches and at least one capacitor. The power converter also includes one or more controllers configured to control the first plurality of switches to selectively couple a first end of the inductor to a first input terminal of the input terminal pair, a second input terminal of the input terminal pair, and a voltage greater than a voltage at the input terminal.

[0012] In some implementations, the at least one capacitor includes a first capacitor and a second capacitor. The output stage is configured to output a first voltage at a first terminal coupled to the first capacitor and a second voltage at a second terminal coupled to the second capacitor.

[0013] In another embodiment, the at least one capacitor includes a first capacitor and a second capacitor.The one or more controllers are further configured to control the second plurality of switches to couple the second end of the inductor to the first capacitor or the second capacitor.

[0014] In yet another embodiment, the power converter further includes a front-end stage configured to synthesize a voltage greater than a voltage at the input terminal.

[0015] In some implementations, the magnetic stage is configured to provide an output voltage between zero volts and twice the voltage at the input terminal while having no right half-plane zero in a control-to-output transfer function of the magnetic stage.

[0016] In another embodiment, the magnetic stage is a first magnetic stage and the inductor is a first inductor. The power converter further includes a second magnetic stage. The second magnetic stage includes a third plurality of switches and a second inductor.

[0017] In yet another embodiment, the one or more controllers are further configured to control a third plurality of switches to selectively couple the first end of the second inductor to a first input terminal of the input terminal pair, a second input terminal of the input terminal pair, and a voltage greater than the voltage at the input terminal.

[0018] In some implementations, the output stage is coupled to the first magnetic stage and the second magnetic stage.

[0019] In another embodiment, the first magnetic stage is configured to output a first voltage, the second magnetic stage is configured to output a second voltage, and the output stage is configured to synthesize at least a third voltage different from the first voltage or the second voltage.

[0020] In yet another embodiment, the first and second magnetic stages are connected in parallel at their inputs.

[0021] In some embodiments, the first magnetic stage and the second magnetic stage are connected in cascade.

[0022] In another embodiment, the power converter further includes a front-end stage configured to provide a voltage greater than a voltage at the input terminal.

[0023] In yet another embodiment, the third voltage is the sum of the first voltage and the second voltage.

[0024] In some embodiments, the second plurality of switches includes a first switch, a second switch, a third switch, and a fourth switch, the at least one capacitor includes a first capacitor, and the power converter further includes a second capacitor, wherein the first switch is coupled between the output of the first magnetic stage and a first terminal of the first capacitor, the second switch is coupled between the second terminal of the first capacitor and the second terminal of the pair of input terminals, the third switch is coupled between the second terminal of the first capacitor and the output of the second magnetic stage, the fourth switch is coupled between the first terminal of the first capacitor and the first terminal of the second capacitor, and the second terminal of the second capacitor is coupled to the output of the second magnetic stage.

[0025] In another embodiment, when the first switch and the second switch are in the first state and the third switch and the fourth switch are in the second state, the first capacitor is charged to the first voltage, and when the third switch and the fourth switch are in the first state and the first switch and the second switch are in the second state, the second capacitor is charged to the first voltage.

[0026] In yet another embodiment, the output stage is configured to output a first voltage, a second voltage, and a third voltage.

[0027] In some embodiments, the third voltage is twice the second voltage minus the first voltage.

[0028] In another embodiment, the second plurality of switches includes a first switch, a second switch, a third switch, and a fourth switch, the at least one capacitor includes a first capacitor, and the power converter further includes a second capacitor. A first terminal of the first switch is coupled to the output of the first magnetic stage and the output of the second magnetic stage, and a second terminal of the first switch is coupled to the first terminal of the first capacitor. A first terminal of the second switch is coupled to the output of the first magnetic stage and the output of the second magnetic stage, and a second terminal of the second switch is coupled to the second terminal of the first capacitor. A first terminal of the third switch is coupled to the output of the first magnetic stage and the output of the second magnetic stage, and a second terminal of the third switch is coupled to the second terminal of the first capacitor. A fourth switch is coupled between the first terminal of the first capacitor and the first terminal of the second capacitor. The second terminal of the second capacitor is coupled to the output of the second magnetic stage.

[0029] In yet another embodiment, when the first and second switches are in the first state and the third and fourth switches are in the second state, the first capacitor is charged to a voltage equal to the second voltage minus the first voltage. When the third and fourth switches are in the first state and the first and second switches are in the second state, the second capacitor is charged to a voltage equal to the second voltage minus the first voltage.

[0030] In some implementations, the output stage is configured to output a first voltage, a second voltage, and a third voltage.

[0031] In another embodiment, the output stage is configured to synthesize at least three different output voltages.

[0032] In yet another embodiment, the output stage is configured to synthesize one or more output voltages ratiometrically related to the output voltage of the magnetic stage.

[0033] In some implementations, the output stage is configured to synthesize a second voltage that is 1.5 times the first voltage.

[0034] In another embodiment, the output stage is configured to synthesize a third voltage that is 0.5 times the first voltage.

[0035] In yet another embodiment, the output stage is configured to output a first voltage, a second voltage that is 1.5 times the first voltage, and a third voltage that is 0.5 times the first voltage.

[0036] In some implementations, the at least one capacitor includes at least seven capacitors and the second plurality of switches includes at least twelve switches.

[0037] In another embodiment, the power converter further includes a front-end stage configured to synthesize a voltage level greater than the voltage at the input terminal.

[0038] In yet another embodiment, the magnetic stage is further configured to selectively couple the first end of the inductor to a first input terminal of the pair of input terminals by operating the first switch. The magnetic stage is further configured to selectively couple the first end of the inductor to a second input terminal of the pair of input terminals by operating the second switch. The magnetic stage is further configured to selectively couple the first end of the inductor to a voltage greater than a voltage at the input terminal by operating the third switch.

[0039] In some implementations, one or more controllers are configured to control first, second, and third switches in the magnetic stage to generate a desired voltage output from the magnetic stage.

[0040] In another embodiment, the one or more controllers are further configured to receive one or more signals corresponding to the load current and provide feed-forward control to generate the desired voltage based on the received one or more signals.

[0041] In yet another embodiment, one or more controllers are configured to control the magnetic stage to synthesize a desired voltage lower than the voltage at the input terminal by operating a first switch to couple a first input terminal of the input terminal pair to the first end of the inductor during one phase of a switching cycle of the magnetic stage, and operating a second switch to couple a second input terminal of the input terminal pair to the first end of the inductor during another phase of the switching cycle of the magnetic stage.

[0042] In some embodiments, the one or more controllers are configured to control the magnetic stage to synthesize a desired voltage that is higher than the voltage at the input terminal by operating a first switch to couple a first input terminal of a pair of input terminals to a first end of an inductor during one phase of a switching cycle of the magnetic stage, and operating a third switch to couple a voltage greater than the voltage at the input terminal to the first end of the inductor during another phase of the switching cycle of the magnetic stage.

[0043] In another embodiment, one or more controllers are configured to control the magnetic stage to synthesize a desired voltage by operating a second switch to couple a second input terminal of the pair of input terminals to a first end of an inductor during one phase of a switching cycle of the magnetic stage, and operating a third switch to couple a voltage greater than a voltage at the input terminal to the first end of the inductor during another phase of the switching cycle of the magnetic stage.

[0044] In yet another embodiment, one or more controllers are configured to control the magnetic stage to synthesize a desired voltage by operating a first switch to couple a first input terminal of a pair of input terminals to a first end of an inductor during a first phase of a switching cycle of the magnetic stage, operating a third switch to couple a voltage greater than a voltage at the input terminal to the first end of the inductor during a second phase of a switching cycle of the second stage, and operating a second switch to couple a second input terminal of the pair of input terminals to the first end of the inductor during a third phase of the switching cycle of the magnetic stage.

[0045] Furthermore, according to some embodiments, a method is provided. The method includes drawing power at a pair of input terminals of a power converter coupled to opposite terminals of a voltage source. The method also includes selectively coupling a first end of an inductor in a magnetic stage of the power converter to a first input terminal of the pair of input terminals, a second input terminal of the pair of input terminals, and a voltage greater than a voltage at the input terminals to generate a voltage level. The method also includes synthesizing an output voltage in an output stage of the power converter that receives the voltage level.

[0046] In some implementations, the method further includes outputting a first voltage at a first terminal of a first capacitor coupled to the output stage.The method further includes outputting a second voltage at a second terminal of a second capacitor coupled to the output stage.

[0047] In another embodiment, the method further includes selectively coupling the second end of the inductor to the first capacitor and the second capacitor.

[0048] In yet another embodiment, the method further includes receiving a voltage from a front end stage of the power converter that is greater than the voltage at the input terminal.

[0049] In some implementations, the method further includes synthesizing a voltage in a front-end stage of the power converter that is greater than the voltage at the input terminal.

[0050] In another embodiment, the method further includes providing a voltage level from the magnetic stage between zero volts and twice the voltage at the input terminal while having no right half plane zero in a control-to-output transfer function of the magnetic stage.

[0051] In yet another embodiment, the magnetic stage is a first magnetic stage and the method further includes selectively coupling a first end of a second inductor in a second magnetic stage to a first input terminal of the pair of input terminals, a second input terminal of the pair of input terminals, and a voltage greater than a voltage at the input terminals.

[0052] In some implementations, the output stage is coupled to the first magnetic stage and the second magnetic stage.

[0053] In another embodiment, the method further includes outputting the first voltage from the first magnetic stage, outputting the second voltage from the second magnetic stage, and outputting the output voltage from the output stage as a third voltage.

[0054] In yet another embodiment, the first magnetic stage and the second magnetic stage are connected in parallel with their inputs.

[0055] In some embodiments, the first magnetic stage and the second magnetic stage are connected in cascade.

[0056] In another embodiment, the third voltage is the sum of the first voltage and the second voltage.

[0057] In yet another embodiment, the method further includes setting the first switch and the second switch of the output stage to a first state, and setting the third switch and the fourth switch of the output stage to a second state, thereby charging the first capacitor to the first voltage. The method further includes setting the third switch and the fourth switch of the output stage to the first state, and setting the first switch and the second switch of the output stage to the second state, thereby charging the second capacitor to the first voltage.

[0058] In some implementations, the method further includes outputting the first voltage, the second voltage, and the third voltage from the output stage.

[0059] In another embodiment, the third voltage is twice the second voltage minus the first voltage.

[0060] In yet another embodiment, the method further includes setting the first switch and the second switch of the output stage to a first state, and setting the third switch and the fourth switch of the output stage to a second state, thereby charging the first capacitor to a voltage equal to the second voltage minus the first voltage. The method further includes setting the third switch and the fourth switch of the output stage to the first state, and setting the first switch and the second switch of the output stage to the second state, thereby charging the second capacitor to a voltage equal to the second voltage minus the first voltage.

[0061] In some implementations, the method further includes outputting the first voltage, the second voltage, and the third voltage from the output stage.

[0062] In another embodiment, the method further includes synthesizing at least three different output voltages in the output stage.

[0063] In yet another embodiment, the method further includes synthesizing one or more output voltages ratiometrically related to voltage levels output by the magnetic stages.

[0064] In some implementations, the method further includes synthesizing, in the output stage, the output voltage to be 1.5 times the voltage level output by the magnetic stage.

[0065] In another embodiment, the method further includes synthesizing, in the output stage, the output voltage to be 0.5 times the voltage level output by the magnetic stage.

[0066] In yet another embodiment, the method further includes outputting, from the output stage, the voltage level output from the magnetic stage, a first voltage that is 1.5 times the voltage level output from the magnetic stage, and a second voltage that is 0.5 times the voltage level output from the magnetic stage.

[0067] In some implementations, the method further includes synthesizing a voltage in a front-end stage of the power converter that is greater than the voltage at the input terminal.

[0068] In another embodiment, the method further includes selectively coupling the first end of the inductor to a first input terminal of the pair of input terminals by operating a first switch. The method further includes selectively coupling the first end of the inductor to a second input terminal of the pair of input terminals by operating a second switch. The method further includes selectively coupling the first end of the inductor to a voltage greater than a voltage at the input terminal by operating a third switch.

[0069] In yet another embodiment, the method further includes receiving, by the one or more controllers, one or more signals corresponding to the load current, and providing, by the one or more controllers, feed-forward control to generate a voltage level at a desired voltage based on the received one or more signals.

[0070] In some embodiments, the method further includes controlling, by the one or more controllers, the magnetic stage to synthesize a voltage level at a voltage lower than a voltage at the input terminals by operating a first switch to couple a first input terminal of the pair of input terminals to the first end of the inductor during one phase of a switching cycle of the magnetic stage, and operating a second switch to couple a second input terminal of the pair of input terminals to the first end of the inductor during another phase of the switching cycle of the magnetic stage.

[0071] In another embodiment, the method further includes controlling, by the one or more controllers, the magnetic stage to synthesize a voltage level at a voltage higher than a voltage at the input terminal by operating a first switch to couple a first input terminal of the pair of input terminals to a first end of the inductor during one phase of a switching cycle of the magnetic stage, and operating a third switch to couple a voltage greater than the voltage at the input terminal to the first end of the inductor during another phase of the switching cycle of the magnetic stage.

[0072] In yet another embodiment, the method further includes controlling, by the one or more controllers, the magnetic stage to synthesize the voltage level by operating a second switch to couple a second input terminal of the pair of input terminals to the first end of the inductor during one phase of a switching cycle of the magnetic stage, and operating a third switch to couple a voltage greater than the voltage at the input terminal to the first end of the inductor during another phase of the switching cycle of the magnetic stage.

[0073] In some embodiments, the method further includes controlling, by one or more controllers, the magnetic stage to synthesize the voltage level by operating a first switch to couple a first input terminal of the pair of input terminals to a first end of an inductor during a first phase of a switching cycle of the magnetic stage, operating a third switch to couple a voltage greater than a voltage at the input terminal to the first end of the inductor during a second phase of the switching cycle of the magnetic stage, and operating a second switch to couple a second input terminal of the pair of input terminals to the first end of the inductor during a third phase of the switching cycle of the magnetic stage.

[0074] Before explaining in detail example embodiments consistent with the present disclosure, it should be understood that the present disclosure is not limited in its application to the details and arrangements of construction set forth in the following description or illustrated in the accompanying drawings. The present disclosure can be practiced and carried out in various ways. Furthermore, it should be understood that the phraseology and terminology employed herein and in the Abstract are for descriptive purposes only and should not be construed as limiting.

[0075] It is to be understood that both the foregoing general description and the following detailed description are explanatory only and are not restrictive of the subject matter, as claimed. BRIEF DESCRIPTION OF THE DRAWINGS

[0076] The accompanying drawings, which are incorporated in and constitute a part of this specification, illustrate and, together with the embodiments, serve to explain the principles of various exemplary embodiments.

[0077] Figure 1A is a block diagram of an exemplary radio frequency (RF) power amplifier (PA) system utilizing multiple power supply levels and a power supply modulator to select from the multiple power supply levels.

[0078] Figure 1B is a block diagram of an example RF amplifier system including a multiple-output power generator, including a single-inductor multiple-output boost converter, a power modulator, and a filter.

[0079] Figure 2A is a schematic diagram of an example dual-output single-input multiple-output (SIMO) converter based on a 4-switch buck-boost converter.

[0080] Figure 2B is a schematic diagram of an example circuit where two outputs can be synthesized using two separate 4-switch buck-boost converters.

[0081] Figure 2C is a schematic diagram of an example circuit in which two different types of power converters can be used to combine two outputs.

[0082] Figure 3A is a schematic diagram of an example circuit capable of non-right half plane zero (NRHPZ) conversion with a boost function.

[0083] Figure 3B is a schematic diagram of an example circuit in which the switches are implemented as metal oxide semiconductor field effect transistors (MOSFETs).

[0084] Figure 4 is a schematic diagram of an example circuit for implementing a 3-level magnetic converter with MOSFETs having a rated blocking voltage lower than the highest possible output voltage.

[0085] Figure 5 is a schematic diagram of an example circuit for implementing a 3-level magnetic converter using flying capacitors.

[0086] Figure 6A is a schematic diagram of an example circuit utilizing an interleaved switched-capacitor front-end stage.

[0087] Figure 6B is a schematic diagram of an example circuit utilizing a multiple-input multiple-output buck converter.

[0088] Figure 6C is a schematic diagram of an example circuit utilizing an interleaved switched-capacitor front-end stage and a multiple-input multiple-output buck converter.

[0089] Figure 7 is a schematic diagram of an example circuit that can be used as a reconfigurable switched capacitor front-end stage.

[0090] Figure 8 is a schematic diagram of an example circuit that can be used as an interleaved reconfigurable switched capacitor front-end stage.

[0091] Figure 9 is a schematic diagram of an example circuit including an NRHPZ converter having a magnetics-based front-end stage based on a buck-boost converter.

[0092] Figure 10 is a schematic diagram of an example circuit including an NRHPZ converter with a buck-boost converter-based magnetic front-end stage and using an active clamping structure.

[0093] Figure 11 is a schematic diagram of an example circuit that utilizes a flying capacitor to provide a switching voltage level greater than the input voltage.

[0094] Figure 12 is a schematic diagram of an example circuit with another topology for generating desired switching levels.

[0095] Figure 13 is a schematic diagram of an example circuit utilizing an interleaving circuit, in which two flying capacitors can be alternately connected to synthesize a voltage higher than the input voltage.

[0096] Figure 14A is a block diagram of an example circuit including two NRHPZ converters, where inputs of the two NRHPZ converters are connected to an energy source and outputs of the two NRHPZ converters are connected to inputs of a switched capacitor converter.

[0097] Figure 14B is a block diagram of an example circuit including two NRHPZ converters in cascade, where the outputs of the two NRHPZ converters are connected to the input of a switched capacitor converter.

[0098] Figure 15 is a schematic diagram of an example circuit including a boost front-end stage shared by two NRHPZ converters, wherein an input of the NRHPZ converter is connected to the boost front-end stage, and an output of the NRHPZ converter is connected to an input of a switched capacitor converter.

[0099] Figure 16A is a schematic diagram of an example circuit including two NRHPZ converters, wherein inputs of the NRHPZ converters are connected to an energy source, and wherein outputs of the NRHPZ converters are connected to inputs of a switched capacitor converter to generate a third voltage output.

[0100] Figure 16B is a schematic diagram of another example circuit including two NRHPZ converters, wherein inputs of the NRHPZ converters are connected to an energy source, and wherein outputs of the NRHPZ converters are connected to a switched capacitor converter to generate a third voltage output.

[0101] Figure 17A is a block diagram of an example circuit utilizing an NRHPZ converter and a multiple-output switched-capacitor converter.

[0102] Figure 17B is a schematic diagram of an example circuit having a switched capacitor front end and a multiple-output switched capacitor converter capable of outputting voltages up to three times the input voltage.

[0103] Figure 17C is a schematic diagram of an example circuit having a multiple-output switched-capacitor converter capable of outputting voltages up to 1.5 times the input voltage.

[0104] Figure 18A is a block diagram of an example circuit illustrating how an NRHPZ controller may interact with and control an NRHPZ converter using various signaling and various feedback and reference signals.

[0105] Figure 18B is a block diagram of an example circuit illustrating the internal workings of an NRHPZ converter in greater detail.

[0106] Figure 19 is a flow chart of an example process for controlling a magnetic regulation stage of the circuit disclosed herein.

[0107] Figure 20 is a flow chart of an example process for controlling a magnetic regulation stage of the circuit disclosed herein using three-phase control.

[0108] Figure 21 is a flow chart of an example process for controlling the magnetic regulation stage of the circuit disclosed herein during two operating cycles. DETAILED DESCRIPTION

[0109] Reference will now be made in detail to embodiments of the present disclosure, specific examples of which are illustrated in the accompanying drawings.

[0110] In the following embodiments, many specific details related to the concepts, circuits, systems, system architectures, methods and techniques of the disclosed subject matter and the environment in which such concepts, circuits, systems, system architectures, methods and techniques are operated are set forth to provide a thorough understanding of the disclosed subject matter. However, after reading the embodiments provided herein, it will be apparent to those skilled in the art that the disclosed subject matter can be put into practice without such specific details. It will also be apparent to those skilled in the art that, in order to avoid making unnecessary complication of the description of the concepts, circuits, systems, system architectures, methods and techniques described herein, certain features well known in the art are not described in detail. In addition, it should be understood that the embodiments provided below are examples, and it is contemplated that other concepts, circuits, systems, system architectures, methods and techniques within the scope of the disclosed subject matter are present.

[0111] The disclosure herein includes a discussion of certain concepts that will be understood by one of ordinary skill in the art and, therefore, is not discussed in further detail to avoid unnecessarily complicating the description of the concepts, circuits, systems, system architectures, methods, and techniques described herein. For example, one of ordinary skill in the art will recognize that the connections between the components described herein (e.g., amplifiers, inductors, resistors, capacitors, switches, diodes, sources, subsystems) can be achieved by wires, circuit board traces on a printed circuit board (PCB), or any other means of electrically and / or mechanically connecting the components together. One of ordinary skill in the art will also understand that connection can mean electrical connection, mechanical connection, or both electrical and mechanical connection.

[0112] Those skilled in the art will also understand what is meant when discussing certain circuit components or subsystems herein, such as inductors, resistors, capacitors, switches, amplifiers, filters, and energy sources. For example, a switch can be implemented as a metal oxide semiconductor field effect transistor (MOSFET), a bipolar junction transistor (BJT), a silicon controlled rectifier (SCR), an insulated gate bipolar transistor (IGBT), a diode, or any other component known to those skilled in the art for providing a switching function in an electronic device. Those skilled in the art will recognize how to drive these components (i.e., provide bias and / or control signals to these components) to switch between an "on" state in which current flows through the component and an "off" state in which current does not flow through the component. Those skilled in the art will understand that these circuit components have terminals for connecting to wires or circuit board traces. Therefore, the following embodiments and / or claims may refer to one or more terminals of a component to convey how the component is connected relative to other components of the circuit. As used herein, the term "energy storage element" should be considered to include any type of energy storage element (e.g., a capacitor or inductor, as just two examples).

[0113] Those skilled in the art will also recognize that electrical components may not be perfect and may fail at certain levels of current and / or voltage. Accordingly, a component may be provided with a rating (e.g., a voltage rating or current rating for the component) that indicates the maximum level of current or voltage that the component is designed to withstand and above which the component may fail. Those skilled in the art will also understand that losses may occur in circuit components and connections. Thus, those skilled in the art will recognize that when voltages and currents are discussed herein, these voltages and currents may be approximate and, in practice, may deviate from the described values ​​to some extent (e.g., 1% to 30% from the described or target or ideal values).

[0114] The concepts, circuits, systems, system architectures, methods, and techniques described herein relate to power management and conversion. Those skilled in the art will understand certain concepts related to this topic. For example, those skilled in the art will understand what is meant when describing certain types of power converters, such as linear regulators or switch-mode power supplies (SMPSs). Those skilled in the art will also understand what is meant when describing certain types of SMPS power converters, such as buck converters, boost converters, buck-boost converters, or flyback converters. Those skilled in the art will understand that one or more switches in an SMPS are typically operated by a controller at a specific operating frequency (e.g., in the kHz to MHz range). Those skilled in the art will understand that these SMPS converters typically operate in two different phases during each cycle of their operating frequency: a first phase in which one or more switches can be turned on, and a second phase in which one or more switches can be turned off. The output voltage or current can be controlled by varying the period during which one or more switches are turned on or off during each cycle. The percentage of on-time during each cycle can be referred to as the duty cycle.

[0115] Those skilled in the art will appreciate that an SMPS converter can operate in different modes, such as a continuous conduction mode in which the current in the inductor never drops to zero during a cycle, and a discontinuous mode in which the current in the inductor does drop to zero during a cycle. Those skilled in the art will recognize that a controller in an SMPS converter can receive feedback regarding one or more characteristics of the converter and can modify one or more aspects of the converter accordingly to achieve a desired output.

[0116] As used herein, an energy source can be any type of energy source that provides a direct current (DC) voltage. For example, the energy source can be any type of battery, an example of which is a lithium-ion battery. The energy source can also be a DC source converted from an alternating current (AC) source, such as a DC source generated by rectifying an AC source. One of ordinary skill in the art will recognize that a power converter can have input terminals connected to opposite terminals of the energy source to draw power from the energy source. One of ordinary skill in the art will also recognize that a power converter can have output terminals configured to be coupled to a load.

[0117] The power management and conversion techniques described herein are described herein with respect to mobile applications, such as for use in mobile phones. However, the present invention is not limited thereto. The techniques described herein can be applied to any type of electronic device that uses electrical power (e.g., mobile devices, laptops, tablets, personal computers, servers, televisions, base stations).

[0118] Figure 1A An example of a radio frequency (RF) power amplifier (PA) system utilizing multiple power supply levels and a power supply modulator to select from the multiple power supply levels is shown. The system 100 can utilize power supply modulation to provide power to one or more RF power amplifiers 135 (e.g., as may be used in a mobile device). The system 100 includes a power generator 110 having an input configured to couple to an energy source 105, such as a battery (the energy source 105 is shown here in dashed lines because it is not a proper part of the system 100). The power generator 110 receives an input signal (e.g., an input voltage) from the energy source 105 and, in response thereto, can generate a power supply between different voltage rails (e.g., each having a voltage such as Figure 1A 0V, V1, V2, ... V shown in m output different voltage levels (e.g., 0V, V1, V2, ... V m ).

[0119] The system 100 also includes a subsystem 115 that includes a power supply modulator 120, an optional filtering or conditioning circuit 130, and a power amplifier 135, all of which can be connected to different voltage rails. For example, the power supply modulator 120 (e.g., power supply modulator #1) can be connected to a voltage rail and can be configured to switch between multiple voltages of the voltage rail. The filtering or conditioning circuit 130 can optionally be connected to the power supply modulator 120 to filter or condition the voltage signal selected by the power supply modulator 120. The result can be a voltage supply (e.g., V SUPPLY#1). The power amplifier 135 can amplify the RF input signal 140 (e.g., RF IN #1), and the amplified RF signal can be used as the RF output signal 145 (e.g., RF OUT #1) Output. The RF input signal 140 may be, for example, an RF signal to be amplified in a mobile device for wireless transmission as an RF output signal 145.

[0120] like Figure 1A As shown in , system 100 can include any number of subsystems connected to the voltage rails and connected in parallel with each other using their inputs. For example, system 100 can include any number of power supply modulators (e.g., power supply modulator #1, ..., power supply modulator #n), optional filtering or conditioning circuits (e.g., optional filtering or conditioning circuit #1, ..., optional filtering or conditioning circuit #n), and power amplifiers (e.g., power amplifiers PA #1, ..., PA #n). A ground rail 125 can also be connected to various components in system 100. Given the example topology of system 100, multiple subsystems can supply different powers (e.g., V ) to any number of power amplifiers (e.g., PA #1, ..., PA #n) from the same energy source 105 and power generator 110 based on the supply requirements of each power amplifier. SUPPLY #1, ..., V SUPPLY #n).

[0121] although Figure 1A System 100 is shown with one power supply generator 110 supporting multiple power amplifiers, and one power supply modulator and optional filtering or regulation circuit for each power amplifier, but the present disclosure is not limited thereto. One of ordinary skill in the art will recognize that, for example, multiple power supply generators can be used to generate any number of voltage rails, and a single power supply modulator and / or filtering or regulation circuit can be used to provide supply voltages to multiple power amplifiers.

[0122] Figure 1B Another example system 150 is shown that may utilize power supply modulation for providing power to a power amplifier 185 of an RF system. Figure 1B The system 150 may include an energy source 160, a power generator 165, a power modulator 170, an optional filter 180, and a power amplifier 185. For example, the power generator 165 may be implemented with a boost converter circuit (e.g., a single inductor 3-output boost converter) including a single inductor (e.g., L1), three capacitors (e.g., C1, C2, C3), and four switches (e.g., S0, S1, S2, S3). The power modulator 170 may be implemented with three switches (e.g., S m1 、S m2、S m3 ) is implemented with one terminal of each switch connected in common. The optional filter circuit 180 can be implemented as an LC (inductor, capacitor) filter with an inductor (e.g., L2) connected in series with the power supply input of the power amplifier 185, a resistor (e.g., R) and a capacitor (e.g., C4) connected in series with each other and in parallel with the power amplifier 185, and a capacitor (e.g., C5) connected in parallel with the power amplifier 185. The ground rail 175 can be connected to various components in the circuit 150. The power amplifier 185 can amplify the input RF signal 190 (e.g., RF IN ) and outputs the amplified RF signal as an output RF signal 195 (e.g., RF OUT ).although Figure 1B An example implementation of circuit 150 is shown, but the disclosure is not limited thereto. Those skilled in the art will recognize that there are additional ways to configure power generator 165, power modulator 170, and filtering circuit 180.

[0123] In some embodiments, the circuitry shown for system 150 can be used to implement Figure 1A at least a portion of the system 100. For example, Figure 1B The power generator 165 may function as the power generator 110 , the power modulator 170 may function as the power modulator 120 , and the optional filter 180 may function as the optional filtering or conditioning circuit 130 .

[0124] One or more controllers 155 may be operable to control switches in the system 100 and / or system 150. For example, one skilled in the art will recognize that one or more controllers may be used to control switches S0 through S3 and switch S1 via one or more signal lines (e.g., circuit connections) 157, e.g., at a high frequency. m1 To S m3 The on / off state and on / off timing of Figure 1B Only one signal line 157 is shown in FIG, but the system 150 may include separate lines from the controller 155 for each switch in the system 150 to individually control each of the switches. Alternatively, some of the switches in the system 150 may be controlled together with a single signal line, while other switches may be individually controlled with separate signal lines.

[0125] The controller 155 can be used to switch the on / off state and timing of the switches S0 to S3 to charge the three different capacitors C1 to C3 to three different voltages V3 to V1 respectively. The controller can also be used to control the switches S m1 To S m3The controller 155 can select the on / off state and timing of the switches S0 to S3 and S1 to select from the voltages V1, V2, and V3, respectively, for providing the selected voltage to the optional filter 180 or the power amplifier 185. It will be understood by those skilled in the art that the controller 155 can receive one or more input signals 158 such as feedback or feedforward signals via one or more signal lines to determine how to control the switches S0 to S3 and S1. m1 To S m3 For example, the controller 155 may be connected to V SUPPLY To monitor V SUPPLY The voltage at or the current supplied to the power amplifier 185 and the switches S0 to S3 and / or S m1 To S m3 As another example, the controller 155 may monitor the RF signal (e.g., RF IN 190) of the RF signal amplitude, and adjust the switches S0 to S3 and / or S m1 To S m3 The on / off state and / or timing of the circuit 150 can be adjusted to adjust the supply voltage or current to the power amplifier 185 based on the RF signal amplitude. Those skilled in the art will recognize that any number of signals within the circuit 150 (e.g., the input voltage V IN , the current I drawn from the energy source IN 、Inductor current (i L1 and / or L2 ), voltage (V1, V2, V3 and / or V SUPPLY ), the current to the PA 185) can be monitored by the controller 155, and the controller 155 can control the switches of the circuit 150 based on these signals. In some embodiments, the controller 155 can include a feed-forward current shaping controller, such as Figure 18A or Figure 18B Controller 1805 and may be connected to circuit 100 and / or circuit 150, such as Figure 18A or Figure 18B As shown in .

[0126] Those skilled in the art will also recognize that the controller 155 may include circuitry and / or subsystems. For example, the controller 155 may have internal components, such as resistors, capacitors, inductors, diodes, comparators, oscillators, clocks, digital logic components (e.g., latches, flip-flops), and / or amplifiers, for controlling the operating frequency of the converter and determining how to control the system 150 based on the feedback / feedforward signal 158. The controller 155 may also include a voltage regulator or other power supply circuitry for powering the controller 155. The controller may also include protection subsystems, such as voltage or current protection subsystems. For example, these subsystems may prevent the occurrence of overvoltage or undervoltage conditions or overcurrent or undercurrent conditions, such as by sensing when the voltage or current exceeds a predetermined value and, for example, by temporarily shutting down the converter circuit or otherwise mitigating the overvoltage or undervoltage or overcurrent or undercurrent condition, to prevent damage to components in the circuit.

[0127] In some embodiments, the controller 155 may include a processor and a memory. The memory may be programmed with instructions such that, when the processor executes the instructions, it controls the switches of the circuit 150 based on the received feedback / feedforward signal 158. In some embodiments, the components and / or subsystems of the controller 155 may be packaged together, such that the controller 155 is, for example, an integrated circuit (IC) containing these components / subsystems.

[0128] Although not shown, the controller 155 may also receive input command signals. For example, the controller 155 may be configured to receive commands from a user or other device that programs the controller 155 to perform certain functions or otherwise changes the functionality of the controller 155.

[0129] Those skilled in the art will also recognize that the subsystems within the controller 155 can themselves have circuitry. For example, the subsystems within the controller 155 can have internal components such as resistors, capacitors, inductors, diodes, comparators, oscillators, clocks, digital logic components (e.g., latches, flip-flops), and / or amplifiers for controlling the operating frequency of the converter circuit and determining how to control the circuit 150 based on the feedback / feedforward signal 158. In some embodiments, the subsystems themselves can include a processor and memory. The memory can be programmed with instructions such that, when executing the instructions, the processor can output certain signals and / or commands based on certain input signals received by the subsystem.

[0130] In some embodiments, one or more controllers can be used to operate some of the switches in the system, while one or more other controllers can be used to operate other switches in the system. For example, a first set of one or more controllers 155 can be operated to control the on / off state and on / off timing of switches S0 to S3 via a first set of one or more signal lines (e.g., circuit connections) 157, thereby controlling the power generator 165. A second set of one or more controllers 155 can be operated to control the on / off state and on / off timing of switches S0 to S3 via a second set of one or more signal lines (e.g., circuit connections) 157. m1 To S m3 The on / off state and on / off timing of the first group of one or more controllers 155 can be used to control the power modulator 170. In some embodiments, the first group of one or more controllers 155 can operate the switch S m1 To S m3 In some embodiments, the first set of one or more controllers 155 can receive a first set of one or more feedback / feedforward signals 158, and the second set of one or more controllers 155 can receive a second set of feedback / feedforward signals 158, which can be different from the first set of feedback / feedforward signals 158.

[0131] Figure 1A and Figure 1B The circuit shown in may be particularly well suited for discrete power supply modulation. As mentioned above, Figure 1A and Figure 1B The circuit shown in FIG may include two subsystems: (a) a power generator that synthesizes multiple supply voltages from a single input source and may regulate one or more of these supply voltages, and (b) one or more power modulators that each rapidly switches between the supply voltages provided by the power generator to provide a modulated supply voltage to an RF power amplifier. How best to implement these two subsystems may depend on the power level, voltage level, and application space of the RF amplifier system. For many applications using such an RF power amplifier system, such as in mobile devices (e.g., mobile phones), it may be desirable to monolithically integrate the electronics for both the power generator and the power modulator on a single semiconductor die (e.g., in a complementary metal oxide semiconductor (CMOS) process). In some embodiments, it may be desirable to integrate the electronics for the power generator, power modulator, and power amplifier on a single die. In some embodiments (e.g., in high-power applications), it may be desirable to implement the subsystems using discrete components connected to one or more printed circuit boards (PCBs).

[0132] The power generator can be implemented in a variety of different ways. For example, a power generator that provides a ratiometric set of output voltages can be implemented using multiple individual converters, multi-output magnetic converters, multi-output switched capacitor converters, and / or hybrid magnetic / switched capacitor converters. Additionally, a multi-output power generator can be implemented that generates two independently controllable direct current (DC) voltages (e.g., using a magnetic conversion stage) and also uses a differential capacitive energy transfer stage to implement one or more additional DC supply voltages that are ratiometrically distributed between or around the two independently controllable voltages. However, each of these approaches may have limitations that restrict the achievable size, cost, efficiency, and performance (e.g., modulation bandwidth) of a power-modulated RF amplifier system.

[0133] Using multiple separate power converters to generate multiple supply voltages is one approach that can produce a flexible solution, allowing each output voltage to be independently regulated to a desired value independent of input voltage variations and providing the ability to continuously adjust the output voltage over time (e.g., to provide adaptive biasing of a power amplifier). However, such solutions can be large and expensive due to the large number of physically large power supply components (e.g., magnetic components) that may be required. Single inductor multiple output converters (sometimes referred to as "SIMO" converters) can allow multiple output voltages to be regulated independently while requiring only a single magnetic component, somewhat alleviating the size challenges that multiple power converters may face. However, SIMO designs can utilize time-sharing of the inductor to supply multiple outputs, resulting in rapid degradation in performance and efficiency, and rapid increase in control complexity as the number of outputs increases. This characteristic limits the effectiveness of this approach in multi-level power supply modulator systems, which can utilize between three and seven power supply levels to achieve high performance (where even more levels may be desired in some cases).

[0134] Some types of power converters, such as multi-output magnetic converters (e.g., multi-output flyback converters), multi-output switched capacitor converters, and hybrid magnetic / switched capacitor converters, can generate multiple ratiometrically related output voltages while reducing the number of magnetic components required compared to using multiple independent power converters. Multi-output magnetic converters can utilize transformers with scaled turns ratios to generate multiple ratiometrically scaled output voltages. These designs may regulate only a single output, while the ratiometric relationship of the other outputs is approximately maintained by the transformer turns ratio (unless additional "post-regulation" is provided to the other outputs, for example, by using additional linear regulators). The use of transformers can also compromise the efficiency achievable in these designs (often to unacceptable levels), and such designs may suffer from significant cross-regulation between outputs in practice (e.g., one output voltage may vary depending on the load on a different output), which can lead to undesirable performance in RF amplifier systems unless additional "post" regulation is used (which can further compromise performance).

[0135] Some of the limitations of these approaches to multi-output power generation can be addressed by using a hybrid magnetic / switched capacitor circuit with ratiometrically scaled outputs. In one example design, a magnetic regulation stage can independently regulate a single output voltage (independent of the system input voltage), with additional ratiometrically related output voltages synthesized and enforced by the action of a switched capacitor voltage balancer stage. For example, in an m-output power generator, the magnetic stage can take the input voltage V X and regulates a single output voltage V Y , where the switch capacitor voltage acts as a composite voltage k1*V Y 、k2*V Y ,……,k m-1 *V Y , where the constants k1, ..., k m-1 is a rational number determined by the circuit topology and / or switching pattern. Advantages of this approach may include relatively high efficiency and small size requirements for synthesizing multiple related output voltages and relative simplicity of control.

[0136] Another hybrid capacitor / magnetic approach can utilize a magnetics-based power conversion system that can independently control two supply voltages (e.g., V1 and V m ), where the additional m-2 supply voltages are generated by differentially connected switched capacitor converters. This may result in additional levels being distributed with some prescribed relationship to the two independently controlled supply voltages, e.g. spaced uniformly between and / or around them (e.g., adjacent voltage levels are each separated by approximately voltage ΔV). For example, if the converter were to independently regulate V1 and V m, and the other m-2 voltages supplied to the power amplifier are equally spaced between them, this may result in m supply voltages V k =V1+(k-1)*(V m -V1) / (m-1), for k=1...m.

[0137] While perhaps not as flexible as providing true independent control of all voltages, power supply modulation can be used to gain most of the practical benefits (e.g., in terms of power amplifier efficiency) while avoiding the aforementioned limitations associated with true independent voltage level control or ratiometric levels. Furthermore, such a design can offer significant advantages in size, cost, efficiency, and performance compared to other approaches.

[0138] In another circuit variation, two regulated supply voltages can be generated, and a hybrid power generator / supply modulator can be utilized to provide more than two discrete voltage levels to the power amplifier. This can have the advantage of providing three or more voltage levels without requiring a separate power generator element to generate these additional levels, cascaded with a power modulator to select between the levels.

[0139] In some of the example circuits described above, it may be desirable to generate two independently controlled outputs. Figure 2A 、 Figure 2B and Figure 2C Each shows an example circuit that can generate two independently controlled outputs.

[0140] Figure 2A An example circuit 200 is shown, which may include a dual-output single-input multiple-output (SIMO) converter based on a 4-switch buck-boost converter. For example, an inductor L, a decoupling capacitor C B And switches S1, S2, S3 and S5 can be operated together to form a IN The first voltage output V B 4-switch buck-boost converter. Inductor L, decoupling capacitor C A and switches S1, S2, S4 and S5 can be operated together to form a B Different second voltage output V A The 4-switch buck-boost converter, the second voltage output V A It can also be higher or lower than V IN The ground rail (GND) can be coupled to various components in the circuit. Additional optional switches (e.g., S opt,A 、S opt,B ) can be added to the circuit and coupled as shown to achieve a A To output V BIn addition to the separate output decoupling capacitor C A and C B In addition, a differential output decoupling capacitor C D .

[0141] One or more controllers 205 may control switches (e.g., S1, S2, S3, S4, S5, S6) in the circuit 200. opt,A 、S opt,B ) to generate the desired output. The controller 205 can be as follows Figure 1B It should be understood that although the controller 155 is implemented as described above, Figure 2A A single control line is shown in FIG, but in an embodiment, two or more different signal lines 207 may be connected to switches S1 to S5, S opt,A 、S opt,B to control different switches of the circuit 200. In an embodiment, each switch may have its own control line connected thereto. The controller 205 may also receive one or more feedback / feedforward signals from the circuit 200 via one or more feedback / feedforward signal lines 208, through which the controller 205 may receive different feedback / feedforward signals. Such feedback / feedforward signals may be detected or otherwise measured or obtained by one or more sensors (e.g., current sensors and / or voltage sensors and / or impedance sensors and / or power sensors). Since such sensors and their operation and use methods are well known to those of ordinary skill in the art, for the sake of clarity, they are not described in detail herein. Figure 2A Thus, as an example, the feedback / feedforward signal provided to the controller 205 may be related to the voltage V A and / or voltage V B and / or at V A The current sensed at V B The current sensed at and / or the current of the inductor L (i L ) and / or input voltage V IN and / or the current I drawn from the input energy source IN The specific feedback / feedforward signal to be provided to the controller 205 is selected based on various factors including, but not limited to, the specific architecture of the circuit 200. In some embodiments, the controller 205 may include a feedforward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B , connected to circuit 200 as shown in FIG.

[0142] Figure 2BAn example circuit 250 is shown where two separate 4-switch buck-boost converters 252, 254 can be used to synthesize two output V A and V B For example, the inductor L A , capacitor C B The switches S1, S2, S3 and S4 can be operated together to form a first voltage output V B The 4-switch buck-boost converter and the inductor L B , capacitor C A and switches S5, S6, S7 and S8 can be operated together to form a B Different second voltage output V A 4-switch buck-boost converter. The ground rail (GND) can be coupled to various components in the circuit. Differential output decoupling capacitors C can also be included. D To provide output decoupling. One of ordinary skill in the art will appreciate that in some designs, circuit 250 may be modified based on voltage range requirements. For example, in some designs, one converter may be implemented as a 4-switch buck-boost converter, while the other converter may be implemented as a simple buck converter (e.g., to supply two voltages V A and V B The smaller of ) or a simple boost converter (e.g., to supply two voltages V A and V B the larger of .

[0143] One or more controllers 255 can control the switches (e.g., S1, S2, S3, S4, S5, S6, S7, and S8) in the circuit 250 to generate a desired output. The controller 255 can be configured as follows: Figure 1B The controller 155 is implemented as described above, but with different signal lines 257 for controlling different switches of the circuit 250 and with different feedback / feedforward signals (e.g., voltage V A , voltage V B , in V A The current sensed at V B The current sensed at the inductor L A The current (i LA ), inductor L B The current (i LB ), input voltage V IN , the current I drawn from the input energy source IN ) of different feedback / feedforward signal lines 258. In some embodiments, the controller 255 may include a feedforward current shaping controller, such as Figure 18A or Figure 18Bcontroller 1805 and can be as Figure 18A or Figure 18B is connected to the circuit 250 as shown in FIG. Figure 2A Similar to the control line 207 described above, it should be understood that although Figure 2B A single control line 257 is shown in FIG. 2 , but in an embodiment, two or more different signal lines 257 may be connected to switches S1 to S8 for controlling different switches of circuit 250 .

[0144] In some embodiments, one or more controllers can be used to operate some of the switches in the circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 255 can be operated to control the on / off state and on / off timing of switches S1 to S4 via a first set of one or more signal lines (e.g., circuit connections) 257, thereby controlling the buck-boost converter 252. A second set of one or more controllers 255 can be operated to control the on / off state and on / off timing of switches S5 to S8 via a second set of one or more signal lines (e.g., circuit connections) 257, thereby controlling the buck-boost converter 254. In some embodiments, the first set of one or more controllers 255 can operate switches S1 to S4 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 255 can operate switches S5 to S8. In some embodiments, a first set of one or more controllers 255 may receive a first set of one or more feedback / feedforward signals 258, and a second set of one or more controllers 255 may receive a second set of feedback / feedforward signals 258, which may be different from the first set of feedback / feedforward signals 258.

[0145] Figure 2C Another example circuit 275 is shown in which two outputs V A and V B In this example, the output voltage V B can be higher than the output voltage V A Higher output voltage. A 4-switch buck-boost converter can be used to synthesize the output voltage V B For example, the inductor L B , capacitor C B The switches S1, S2, S3 and S4 can be operated together to form a first voltage output V B 4-switch buck-boost converter. The output voltage V B Powered by a step-down converter to synthesize a voltage less than or equal to V B The second independently regulated output voltage V AInductor L A , capacitor C A And switches S5 and S6 can operate together to form a voltage V B Powering the buck converter to provide a second voltage output V A The ground rail (GND) can be coupled to various components in the circuit. It can also include differential output decoupling capacitors C D To provide output decoupling.

[0146] One or more controllers 280 can control the switches (e.g., S1, S2, S3, S4, S5, and S6) in the circuit 275 to generate a desired output. The controller 280 can be as shown for Figure 1B The controller 155 is implemented as described above, but with different signal lines 282 for controlling different switches of the circuit 275, and with different feedback / feedforward signals (e.g., voltage V A , voltage V B , in V A The current sensed at V B The current sensed at the inductor L A The current (i LA ), inductor L B The current (i LB ), input voltage V IN , the current I drawn from the input energy source IN ) of different feedback / feedforward signal lines 283. In some embodiments, the controller 280 may include a feedforward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B , connected to circuit 275 as shown in FIG.

[0147] In some embodiments, one or more controllers can be used to operate some of the switches in the circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 280 can be operated to control the on / off state and on / off timing of switches S1 to S4 via a first set of one or more signal lines (e.g., circuit connections) 282, thereby controlling a four-switch buck-boost converter. A second set of one or more controllers 282 can be operated to control the on / off state and on / off timing of switches S5 and S6 via a second set of one or more signal lines (e.g., circuit connections) 282, thereby controlling a buck converter. In some embodiments, the first set of one or more controllers 280 can operate switches S1 to S4 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 280 can operate switches S5 and S6. In some embodiments, a first set of one or more controllers 280 may receive a first set of one or more feedback / feedforward signals 283, and a second set of one or more controllers 280 may receive a second set of feedback / feedforward signals 283, which may be different from the first set of feedback / feedforward signals 283.

[0148] As mentioned above, it is often desirable to implement power converters that generate one or more controllable DC output voltage levels from a DC voltage (e.g., battery) level input. RF systems in which these converters are used can exhibit fast transient behavior, which can in turn place very fast load transients on the power converter. Furthermore, in systems in which two independent power sources are created, this can manifest as rapid load transfers between the two power sources (i.e., the load can be quickly transferred back and forth between the two generated outputs).

[0149] The load transients mentioned above can have a significant impact on the design of such power converters. In practice, the highest frequency components of such load transitions can be absorbed by the converter's output capacitance (e.g., a single-ended capacitor connected to ground or a differential capacitor placed between the converter outputs). At lower frequencies, such load transitions can be compensated by the converter control loop. It is desirable that the converter control loop generate a low closed-loop output impedance for the converter to reduce the magnitude and duration of output voltage deviations during load transitions.

[0150] Converters in some applications, such as those used in mobile devices (e.g., mobile phones), may be subject to significant size constraints. Consequently, the amount of converter output capacitance that can be placed can be quite limited. Furthermore, in order to achieve a fast response to output voltage change commands, it may be desirable to limit the amount of capacitance placed at the converter output. Providing the converter with a wider closed-loop control bandwidth can help reduce the amount of output capacitance required to suppress the magnitude of voltage deviations caused by load switching. Consequently, there may be a strong incentive to provide the converter with as wide a closed-loop control bandwidth as possible.

[0151] It is perhaps easiest to achieve a high control bandwidth relative to the switching frequency (and a wide bandwidth over which the closed-loop output impedance remains low) for a converter that can respond to load changes by rapidly increasing (or decreasing) the energy delivered to the output from the input (or another energy reserve) (e.g., within a single switching cycle or two), rather than having to instantaneously decrease (or increase) the energy delivered to the output during a transition when the load increases (or decreases) or when, as one skilled in the art would aim for, an increase (or decrease) in the output voltage. Converters capable of providing a single-cycle response typically do not exhibit a right-half-plane zero in their linearized, averaged control-to-output transfer function. Converters that do not exhibit a right-half-plane zero in their linearized, averaged control-to-output transfer function (i.e., have no right-half-plane zero in their control-to-output transfer function) will be referred to herein as "non-right-half-plane zero" or "NRHPZ" converters. For example, a buck converter is an NRHPZ converter, while most other converters—including conventional boost converters and four-switch buck-boost converters—are not NRHPZ converters.

[0152] NRHPZ converters can also be subject to load current feedforward control over a much wider bandwidth than other converters with right-half-plane zeros. Load current feedforward control can provide a way for the converter to quickly compensate for load current slews by sensing changes in the load current and providing feedforward control to the current control loop. This can be done without modifying the closed-loop pole positions of the converter (of the linearized, averaged model) or controlling the output dynamics. This can also change the position of the zero or eliminate the effect of the zero in the converter output impedance, thereby providing a wider frequency range within which the output impedance is low. However, if the converter has a right-half-plane zero, the effect of the zero may not be eliminated (e.g., using an introduced pole), thereby limiting the bandwidth over which load current feedforward control can be used to reduce the converter closed-loop output impedance of these converters. However, load current feedforward control can be an effective method for achieving low closed-loop output impedance over a wide bandwidth in NRHPZ converters.

[0153] In view of the above, for applications that only step down, a buck converter can be a good type of converter for RF applications because it does not have a right derivative plane zero and can achieve low output impedance over a wide frequency range, including by using load current feedforward control. However, in some applications, the converter may still need to provide a voltage boost function for some operating conditions. Therefore, it may be desirable to implement an NRHPZ converter that can provide at least some degree of voltage boost operation. The required voltage boost conversion ratio may depend on the specific application system and operating conditions. In some systems, the voltage boost conversion ratio may not need to be greater than 1.5 or 2 times. In other applications, the voltage boost conversion ratio may need to be greater than 2 times. In addition, in some applications, the converter may have to provide voltage boost conversion under some conditions and voltage step-down conversion under other conditions (e.g., "buck and boost" operation). This article discloses concepts, systems, system architectures, circuits, methods, and techniques that can perform NRHPZ conversion to provide one or more outputs while still providing the ability to provide a certain degree of boost functionality for one or more outputs.

[0154] Non-Right Half Plane Zero (NRHPZ) Converter Circuit

[0155] Figure 3A An example power converter circuit 300 (or more simply, a power converter) is shown that is capable of performing NRHPZ conversion to provide a voltage output as well as some degree of boost functionality. The power converter circuit 300 may be connected to a power supply at an input terminal (shown as connected to a power supply provided at a Figure 3A The dotted line V IN ) is coupled to an input energy source (e.g., V IN ), and a voltage V is generated across the output terminal (shown as OUT ) is coupled to a load at a node (node ​​of ). Circuit 300 is an example of a hybrid magnetic / switched capacitor converter that provides NRHPZ conversion. Circuit 300 may include a front-end stage 310 having a switching network and at least one energy storage element (e.g., a switched capacitor (SC) stage shown here as an SC multiplier stage) and a magnetic stage 320. Front-end stage 310 may include a switched capacitor circuit connected to an input energy source (e.g., V IN ) and can be synthesized to be essentially the input voltage V IN A multiple (in this example embodiment, approximately twice) of the voltage V H (where voltage V IN 、V H Measured relative to a reference potential, which in this example embodiment corresponds to common ground 330 ).

[0156] In some embodiments, the front-end stage 310 of the circuit 300 can operate at a first frequency. During the first half of a cycle at the first frequency, the switch S (in response to a control signal provided thereto) 1A and S 1B may be biased or otherwise controlled or otherwise placed in its "on" state (also referred to as the switch being "closed" or "in a conductive state such that a low impedance signal path exists between the terminals of the switch"), and the switch S 2A and S 2B The switch S may be biased, controlled, or otherwise placed into its "off" state (also referred to as the switch being "open" or "in a conductive state such that a high impedance signal path exists between the terminals of the switch"). 1A 、S 1B 、S 2A and S 2B This configuration allows capacitors such as C f The energy storage element (e.g., a flying capacitor) is charged to a voltage V IN .

[0157] During the second half of the cycle at the first frequency, the switch S 2A and S 2B can be turned on, and the switch S 1A and S 1B This allows the capacitor C f The energy is released to the output of the front-end stage and the voltage V on capacitor C1 is allowed to HI is charged to V IN (2*V IN -V IN (Source) = V IN ). Therefore, the voltage V H (Voltage on capacitor C1 with respect to common ground) can be 2*V IN (Source voltage V IN +The voltage across capacitor C1 is V HI ).

[0158] In this example embodiment, the magnetic stage 320 is shown as a three-level buck derived magnetic converter (referred to herein as a 3-level buck converter) having an inductor L having a first end (e.g., a component terminal) that can be connected to any of three voltages: V H (eg, as output from front-end stage 310), V IN and common 330 (eg, common ground or 0V), the second end being connected to the output V OUTFor example, the inductor L, capacitor C2, and switches S3 to S5 may function together to operate as a 3-level buck converter.

[0159] Switches S3, S4, and S5 can operate at a second operating frequency. In some embodiments, the second operating frequency can be the same as the switch S 1A 、S 1B 、S 2A and S 2B The first operating frequency at which the circuit 300 operates is different (e.g., higher, lower). For example, the front-end stage 310 of the circuit 300 can operate at a first frequency independently of the magnetic stage 320 of the circuit 300, which can operate at a second frequency. However, the present disclosure is not limited in this regard, and in some embodiments, the first operating frequency can be the same as the second operating frequency.

[0160] When switch S3 is on and switches S4 and S5 are off, the buck converter can operate at V X Receive V H Because the front-end stage 310 (eg, switched capacitor multiplier) has charged capacitor C1 to V IN (making V HI Equal to V IN ), so when switch S3 is turned on and switches S4 and S5 are turned off, V X The voltage V H Can be 2*V IN (V HI +V IN , where V HI =V IN ). When switch S3 is off and switch S4 is on, the buck converter can X The voltage from the energy source V IN Receive V IN When switches S3 and S4 are off and switch S5 is on, the buck converter can receive a common input voltage (eg, common ground or 0V) from common 330 .

[0161] In order to synthesize a low output voltage V OUT (lower than V IN ), V X The input voltage of the buck converter at the second frequency can be between the phases of each cycle (phase) V IN and 0V. In order to synthesize a high output voltage V OUT (between V IN With V H Between), V X The input voltage of the buck converter at the second frequency can be adjusted between the phases of each cycle at VH With V IN Switch alternately between. The synthesis is close to V IN The output voltage V OUT There are several possibilities. As an example, V X The input voltage of the buck converter at the second frequency can be adjusted between the phases of each cycle at V H As another example, V X The input voltage of the buck converter at the second frequency can be varied between the three phases of each cycle with V IN 、V H The mode switches alternately between 0V and 0V (for example, using three-phase operation as described below, among other possibilities). Using the above options, the output voltage V OUT Can be controlled between 0V and close to 2*V IN between them without creating a right-half-plane zero in the magnetic stages.

[0162] One or more controllers 305 may control switches (eg, S 1A 、S 1B 、S 2A 、S 2B , S3, S4 and S5) to generate the required output voltage V OUT . The controller 305 can be as follows Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 300, there are different signal lines 307 for controlling different switches of the circuit 300, and different feedback / feedforward signal lines 308 for detecting different feedback / feedforward signals (for example, the voltage V OUT , voltage V X , voltage V H , voltage V HI , in V OUT The load current sensed at the inductor L (i L ), input voltage V IN , the current I drawn from the input energy source IN ). Other feedback / feedforward signals may also be used. After reading the disclosure provided herein, one of ordinary skill in the art will understand how to select an appropriate feedback / feedforward signal (or an appropriate characteristic of the system to use as feedback / feedforward quantity) for a particular application. In some embodiments, the controller 300 may include a feedforward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B , connected to circuit 300 as shown in FIG.

[0163] In some embodiments, one or more controllers may be used to operate some switches in a circuit, while one or more other controllers may be used to operate other switches in the circuit. For example, a first set of one or more controllers 305 may be operable to control switches S via a first set of one or more signal lines (e.g., circuit connections) 307. 1A 、S 1B 、S 2A and S 2B The first set of one or more controllers 305 may be operable to control the on / off state and on / off timing of switches S3, S4, and S5 via a second set of one or more signal lines (e.g., circuit connections) 307, thereby controlling the magnetic stage 320. In some embodiments, the first set of one or more controllers 305 may be operable to operate switches S3, S4, and S5 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 305 may operate switches S3, S4, and S5. 1A 、S 1B 、S 2A and S 2B For example, the duty cycle of controlling the switches of the front-end stage 310 may depend on the detailed topology and operating mechanism (e.g., slow switching limit vs. fast switching limit). In some embodiments, the first set of one or more controllers 305 may control the switches S with a duty cycle of approximately 50%. 1A 、S 1B 、S 2A and S 2B In some embodiments, the first stage switch (e.g., S 1A 、S 1B 、S 2A 、S 2B ) can operate independently of the switches of the second stage (e.g., S3, S4, S5). In some embodiments, the first set of one or more controllers 305 can receive a first set of one or more feedback / feedforward signals 308, and the second set of one or more controllers 305 can receive a second set of feedback / feedforward signals 308 that can be different from the first set of feedback / feedforward signals 308.

[0164] Implementing the 3-level magnetic converter of circuit 300 may require two unidirectional voltage blocking switches (S3, S5) and one bidirectional blocking switch (S4). Switches S3 and S5 may both be rated for 2*V IN The blocking voltage (assuming that according to the switch configuration, 2*V IN voltage drop), while switch S4 can be rated for + / -V INThe blocking voltage (assuming that, depending on the switch configuration, it will produce V in either direction) IN pressure drop).

[0165] In a metal oxide semiconductor (MOS) process, the switches can be implemented as N-channel or P-channel field effect transistors (FETs). For example, switches S3 and S5 can both include N-channel MOSFETs, and switch S4 can include an N-channel MOSFET with body switch functionality. Switches can also include a combination of P-channel and N-channel MOSFETs. For example, switch S3 can include a P-channel MOSFET, switch S5 can include an N-channel MOSFET, and switch S4 can include an N-channel MOSFET with body switch functionality.

[0166] Figure 3B An example circuit 350 is shown where switches S3 and S5 are implemented as MOSFETs, both rated for 2*V IN The blocking voltage of the switch S4 is a MOSFET rated at V IN Bidirectional (+ / -) blocking voltage. Figure 3B The front-end stage 355 can be as Figure 3A The front-end stage 310 may be constructed as described, or alternatively may include a magnetic-based front-end boost stage (e.g., see Figure 9 、 Figure 10 ). The switches S3, S4 and S5 of the magnetic stage 365 can be as described above with respect to Figure 3A The description is controlled to provide a voltage substantially equal to V H (For example, 2*V IN ), V IN or 0V voltage V X In addition, V IN With V H Between 0V and V IN Between and V IN The output voltage near V OUT You can use the above Figure 3A The alternating switching scheme described was synthesized.

[0167] One or more controllers 370 may control switches in the circuit 350 (eg, S3, S4, S5) and switches within the front-end stage 355 (eg, see Figure 3A ) to generate the required output voltage V OUT . The controller 370 can be as follows Figure 1BThe controller 155 is implemented as described above, but based on the different architecture of the circuit 350, there are different signal lines 373 for controlling different switches of the circuit 350, and different feedback / feedforward signal lines 374 for detecting different feedback / feedforward signals (for example, the voltage V OUT , voltage V X , voltage V H , voltage V HI , in V OUT The load current sensed at the inductor L (i L ), input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 370 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B Connected to circuit 350 as shown.

[0168] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 370 can be operated to control the on / off state and on / off timing of switches in the front-end stage 355 via a first set of one or more signal lines (e.g., circuit connections) 373, thereby controlling the front-end stage 355. A second set of one or more controllers 370 can be operated to control the on / off state and on / off timing of switches S3, S4, and S5 via a second set of one or more signal lines (e.g., circuit connections) 373, thereby controlling the magnetic stage 365. In some embodiments, the first set of one or more controllers 370 can operate the switches in the first stage 355 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 370 can operate switches S3, S4, and S5. For example, the duty cycle of the switches in the first stage can depend on the detailed topology and operating mechanism (e.g., slow switching limit vs. fast switching limit). In some embodiments, the first set of one or more controllers 370 can control the switches of the front-end stage 355 at a duty cycle of approximately 50%. In some embodiments, the switches of the front-end stage 355 can operate independently of the switches (e.g., S3, S4, S5) of the magnetic stage 365. In some embodiments, the first set of one or more controllers 370 can receive a first set of one or more feedback / feedforward signals 374, and the second set of one or more controllers 370 can receive a second set of feedback / feedforward signals 374 that can be different from the first set of feedback / feedforward signals 374.

[0169] In some implementations, it may be desirable to use a device rated for less than 2*V IN The blocking voltage of the MOSFET is used to realize the switch in the circuit.

[0170] Figure 4 An example embodiment of a circuit 400 for implementing a 3-level buck converter as described above but with MOSFETs having a lower rated blocking voltage than in the previous examples is shown. The arrangement of switches shown in the magnetic stage 420 can be used in any circuit that provides three voltage levels from which the magnetic stage can be switched. For example, Figure 3A or Figure 3B The switch arrangement shown in can be replaced by Figure 4 The switch arrangement shown in FIG. 1 is used to utilize a step-down device.

[0171] As with the previously discussed example circuits, the example circuit 400 includes a front-end stage 410 and a magnetic stage 420. The front-end stage 410 may be implemented as previously discussed (e.g., see Figure 3A The front-end stage 310 is based on the magnetic front-end stage (see, for example, Figure 9 、 Figure 10 )). The magnetic stage 420 can be implemented as a 3-level buck converter, which includes an inductor L having: a first terminal (e.g., a first component terminal or a first end) connected to a node 419, at which any one of the three voltages can be provided; and a second terminal (e.g., a second component terminal or a second end) connected to the output of the circuit 400. In this example embodiment, the three voltages correspond to: (1) a voltage V H (eg, as the output voltage from the front-end stage 410 (where the front-end stage 410 corresponds to the SC multiplier)); (2) the voltage V IN (eg, corresponding to the input voltage); and a reference potential at node 430 (sometimes also referred to as common 430), where the reference potential corresponds to common ground or 0V.

[0172] Inductor L, capacitor C B The switches S1 to S6 can be operated (i.e., switched between conductive and non-conductive states) to function as a 3-level buck converter. When switches S1 and S5 are on (i.e., biased to their conductive state) and switches S2, S4, and S6 are off (i.e., biased to their non-conductive state), the 3-level buck converter can receive V at node 419. H The input voltage, in this case V X Equal to voltage V H .

[0173] The front-end stage 410 may be configured as an SC multiplier, as described above in conjunction with Figure 3A and Figure 3BAs described above, it is possible to withstand about V IN The voltage (for example, the voltage V HI ) of a charged capacitor (e.g. C1) and a voltage V IN connected so that the voltage V H Close to 2*V relative to common ground IN In this configuration, when switches S1 and S5 of magnetic stage 420 are on and switches S2, S4, and S6 of magnetic stage 420 are off, the voltage V seen at node 419 is H ( Figure 4 Designated as V X ) will be close to 2*V IN .

[0174] Furthermore, when the switches S1 and S4 of the magnetic stage 420 are turned off and the switches S2 and S5 and / or the switches S3 and S6 of the magnetic stage 420 are turned on, the voltage at the node 419 ( Figure 4 Designated as V X ) is essentially equal to the voltage V IN , so the buck converter can receive V IN The input voltage (V X =V IN ).

[0175] When switches S4 and S6 are turned on and switches S3 and S5 are turned off, the buck converter may receive a common input voltage (eg, a common ground or a reference potential of 0V).

[0176] Therefore, a low output voltage (lower than V IN ), so that the IN The value of the voltage as the input voltage V X Provided to 3-level buck converter. That is, in order to synthesize a low output voltage (lower than V IN ), V X The input voltage of the 3-level buck converter can be V IN Volts and below V IN Some reference potential of volts (in Figure 4 In the example implementation, such a reference potential is shown as switching alternately between 0 volts (or ground).

[0177] Likewise, through the operation of switches S1 to S6, in order to synthesize a high output voltage (eg, V IN With V H The voltage between ), the input voltage V X The VH With V IN Switch alternately between.

[0178] The synthesis is close to or equal to V IN There are several possibilities for the output voltage of . As an example, the input voltage V X The V H As another example, the input voltage of the 3-level buck converter at node 419 can be switched between V IN 、V H and 0V (e.g., using three-phase operation as described below, among other possibilities). OUT The voltage that can be controlled to be approximately the reference potential (here 0V) is approximately (or close to) 2*V IN The corresponding voltages are between those that do not result in a right-half-plane zero of the magnetic level.

[0179] The arrangement of the switches in circuit 400 may allow the use of components / devices having voltage ratings and / or current ratings that are reduced compared to the required voltage ratings and / or current ratings of the components / devices used in circuits 300 and 350 (sometimes referred to herein as "voltage-reducing components / devices" or "current-reducing components / devices"). For example, each switch (e.g., S1, S2, S3, S4, S5, and S6) in circuit 400 may have a voltage rating of V IN , although the voltage V H The voltage value is about 2*V IN That is to say, in Figure 4 In an example embodiment, switches S1 , S2 , S3 , S4 , S5 , and S6 may synthesize a voltage at the output of the converter that is greater than the voltage rating of the switches.

[0180] Circuit 400 can be described as including an "active neutral point clamp" or ANPC configuration of switches. For different configurations of switches S1, S2, S3, S4, S5, and S6, the voltage V at node 419 is X As shown in Table 1 below. In Table 1, a "1" listed in the switch column indicates that the switch is on, a "0" listed in the switch column indicates that the switch is off, and an "X" listed in the switch column indicates that the switch can be on or off. "V X The voltages listed in the " column indicate the configuration of the six switches shown in the same row at V X The "Comment" column describes the switch arrangement in this row to output "V X The voltage listed in the " column V X The preferred switching arrangement of is also an alternative switching arrangement for outputting this voltage.

[0181] Table 1

[0182]

[0183] One or more controllers 405 may control switches in the circuit 400 (e.g., S1, S2, S3, S4, S5, S6) and switches within the front-end stage 410 (e.g., see Figure 3A ) to generate the required output voltage V OUT . The controller 405 can be as follows Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 400, there are different signal lines 407 for controlling different switches of the circuit 400, and different feedback / feedforward signal lines 408 for detecting different feedback / feedforward signals (for example, the voltage V OUT , voltage V X , voltage V H , voltage V HI , in V OUT The load current sensed at the inductor L (i L ), input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 405 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B Connections to circuit 400 are shown.

[0184] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 405 can be operated to control the on / off state and on / off timing of switches in a front-end stage 410 via a first set of one or more signal lines (e.g., circuit connections) 407, thereby controlling the front-end stage 410. A second set of one or more controllers 405 can be operated to control the on / off state and on / off timing of switches S1 through S6 via a second set of one or more signal lines (e.g., circuit connections) 407, thereby controlling the magnetic stage 420. In some embodiments, the first set of one or more controllers 405 can operate the switches in the front-end stage 410 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 405 can operate switches S1 through S6. For example, the duty cycle of the switches controlling the front-end stage 410 can depend on the detailed topology and operating mechanism (e.g., slow switching limit versus fast switching limit). In some embodiments, the first set of one or more controllers 405 can control the switches of the front-end stage 410 at a duty cycle of approximately 50%. In some embodiments, the switches of the front-end stage 410 can operate independently of the switches (e.g., S1 to S6) of the magnetic stage 420. In some embodiments, the first set of one or more controllers 405 can receive a first set of one or more feedback / feedforward signals 408, and the second set of one or more controllers 405 can receive a second set of feedback / feedforward signals 408 that can be different from the first set of feedback / feedforward signals 408.

[0185] In some implementations, it may be desirable to reduce the front-end stage (e.g. Figure 3A and Figure 3B Front-end level 310, Figure 4 The energy requirements of the front-end stage 410).

[0186] Figure 5 An example circuit 500 is shown that includes a front-end stage 510 (e.g., an SC multiplier (see, e.g., Figure 3A ), magnetic-based front-end stages (see e.g. Figure 9 、 Figure 10 )), the front-end stage is coupled to the magnetic stage 520 to form a 3-level magnetic converter, as described above, but incorporating a flying capacitor C in the magnetic stage 520 f The front-end stage 510 may be configured as an SC multiplier, as described above in conjunction with Figure 3A and Figure 3B As described above, the charged capacitor (e.g. C1) is subjected to a voltage of about V IN The voltage (for example, the voltage V HI ), so that the voltage VH Close to 2*V relative to common ground IN The magnetic stage 520 may be a flying capacitor multi-level buck converter having an inductor L whose first end (e.g., first component terminal) may be connected to any of a plurality of voltages—here, three voltages—at a node 519. In this example embodiment, the three voltages correspond to: (1) V H (e.g., output from front-end stage 510); (2) V IN ; and (3) a reference potential or common 530 (e.g., common ground or 0V). The second end of the inductor L (e.g., the second component terminal) is connected to the output terminal, at which the output voltage V OUT .

[0187] Flying capacitor C f Can be used to provide a IN to V HI energy transfer, thereby reducing the energy transfer requirements of the SC stage 510. That is, the flying capacitor C f Can be used to change the voltage from V IN passed to the charged capacitor C1 to V HI For example, the V X The voltage V IN The two switching configurations are alternated to ensure that the voltage on capacitor C1 is V IN Towards V HI In this example, capacitor C1 can be charged in two different ways. One way is through the switch of the front-end stage 510, as described above. The other way is by using capacitor C f That is, in the second mode, when switches S2 and S4 are turned on, capacitor C f Can be from V IN When switches S1 and S3 are turned on, capacitor C f Table 2 below shows the voltage V at node 519 for different configurations of switches S1, S2, S3, S4, S5, and S6. X In Table 2, a “1” listed in the switch column indicates that the switch is on, and a “0” in the switch column indicates that the switch is off. “V X The voltages listed in the " column indicate the voltages V achieved for the six switch configurations shown in the same row. X The "Comment" column describes how energy is transferred by the switch arrangement in that row.

[0188] Table 2

[0189]

[0190] In some cases, the front-end stage 510 can be eliminated and the C f All energy is transferred to generate voltage V H For example, when switches S2 and S4 are on and switches S1 and S3 are off, capacitor C f Can be charged to a voltage V IN Basically equal voltage V f Then, with switches S3 and S5 turned on and switches S2 and S4 turned off, the voltage V IN Can be charged to voltage V IN Capacitor C f The voltage V f connected, thus generating a voltage of 2*V IN The corresponding input voltage to the buck converter is V H If the front-end stage 510 is eliminated, the switch S1 may no longer be needed and may be eliminated.

[0191] One or more controllers 505 may control switches in the circuit 500 (e.g., S1, S2, S3, S4, S5, S6) and switches of the front-end stage 510 (e.g., see Figure 3A ) to generate the required output voltage V OUT For example, as previously described, the controller 505 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired output voltage V OUT . The controller 505 can be as follows Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 500, it has different signal lines 507 for controlling different switches of the circuit 500, and has different feedback / feedforward signal lines 508 for detecting different feedback / feedforward signals (for example, the voltage V OUT , voltage V X , voltage V H , voltage V HI , in V OUT The load current sensed at the inductor L (i L ), input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 505 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B Controller 1805 in the example, and can be Figure 18A or Figure 18B Connections to circuit 500 are shown.

[0192] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 505 can be operated to control the on / off state and on / off timing of switches in a front-end stage 510 via a first set of one or more signal lines (e.g., circuit connections) 507, thereby controlling the front-end stage 510. A second set of one or more controllers 505 can be operated to control the on / off state and on / off timing of switches S1 through S6 via a second set of one or more signal lines (e.g., circuit connections) 507, thereby controlling the magnetic stage 520. In some embodiments, the first set of one or more controllers 505 can operate the switches in the front-end stage 510 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 505 can operate switches S1 through S6. For example, the duty cycle of the switches in the first stage can depend on the detailed topology and operating mechanism (e.g., slow switching limit vs. fast switching limit). In some embodiments, the first set of one or more controllers 505 can control the switches of the front-end stage 510 at a duty cycle of approximately 50%. In some embodiments, the switches of the front-end stage 510 can operate independently of the switches (e.g., S1 to S6) of the magnetic stage 520. In some embodiments, the first set of one or more controllers 505 can receive a first set of one or more feedback / feedforward signals 508, and the second set of one or more controllers 505 can receive a second set of feedback / feedforward signals 508 that can be different from the first set of feedback / feedforward signals 508.

[0193] In some implementations, it may be desirable to reduce the amount of capacitance required to implement the converter. For example, it may be desirable to reduce the holding voltage V H The total amount of capacitance required.

[0194] Figure 6A An example circuit 600 is shown that may use a front-end stage 610 that is an interleaved switched capacitor voltage multiplier, rather than the non-interleaved version previously discussed (e.g., see Figure 3A That is, Figure 6A An example circuit 600 is shown for implementing a 3-level magnetic converter, as described above, but with the front-end stage 610 implemented as an interleaved switched capacitor stage.

[0195] The magnetic stage 620 may include an inductor L, a capacitor C B The first terminal of the buck converter can be connected to any of the following three voltages: V H (e.g., the output of the front end 610), V IN, and a common 630 (eg, common ground or 0V), and the second end may be connected to the output V OUT .and Figure 3A Similar to the front end 310, the front end 610 can synthesize an input voltage of approximately V IN Twice the voltage V (relative to the common ground 630) H .

[0196] For example, one or more controllers 605 may operate a switch S 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C 、S 2D , S3, S4 and S5. The switch S of the front-end stage 610 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C and S 2D The front-end stage 610 may be operated at a first frequency, and the switches S3, S4, and S5 of the magnetic stage 620 may be operated at a second frequency. In some embodiments, the first frequency of operation of the front-end stage 610 may be different from (e.g., lower, higher) the second frequency of operation of the magnetic stage 620, and the two stages may be operated independently. However, the present disclosure is not limited thereto, and the first frequency and the second frequency may be the same. During the first half cycle at the first frequency, the switches S 1A 、S 1B 、S 1C and S 1D can be turned on, and the switch S 2A 、S 2B 、S 2C and S 2D This switch configuration allows the capacitor C f1 Charge to voltage V IN and the capacitor C bb Charge to voltage V IN (2*V relative to common ground IN ), provided that the capacitor C f1 Previously charged to voltage V IN During the second half cycle at this frequency, the switch S 2A 、S 2B 、S 2C and S 2D can be turned on, and the switch S 1A 、S 1B 、S 1Cand S 1D This switch configuration allows the capacitor C f2 Charge to voltage V IN and the capacitor C bb Charge to voltage V IN (2*V relative to common ground IN ), provided that the capacitor C f2 Previously charged to voltage V IN Those skilled in the art will recognize that the switch configuration described above for the second half cycle can be used for the first half cycle, and the switch configuration described above for the first half cycle can be used for the second half cycle.

[0197] Then, the 3-level buck converter of the magnetic stage 620 can receive the input voltage V H The voltage level of this input voltage corresponds to the voltage 2*V when switch S3 is turned on and switches S4 and S5 are turned off. IN , and the voltage V when switch S4 is turned on and switches S3 and S5 are turned off IN The corresponding input voltage is 0V, or the input voltage is 0V when the switch S5 is turned on and the switches S3 and S4 are turned off. Figure 6A One benefit of the illustrated interleaved switched capacitor multiplier 610 may be a reduction in the amount of capacitance required to implement the converter, such as capacitors C bb Holding voltage V H Another benefit may be that the operation of the two half-cycle switching configurations discussed above may be used together to achieve a "soft" discharge of the flying capacitor by the second magnetic stage, thereby reducing losses in the switched capacitor stage.

[0198] One or more controllers 605 may control switches (eg, S 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C 、S 2D , S3, S4, S5) to generate the required output voltage V OUT For example, as previously described, the controller 605 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired output voltage V OUT Controller 605 can be as follows Figure 1BThe controller 155 is implemented as described above, but based on the different architecture of the circuit 600, it has different signal lines 607 for controlling different switches of the circuit 600, and has different feedback / feedforward signal lines 608 for detecting different feedback / feedforward signals (for example, the voltage V OUT , voltage V X , voltage V H , in V OUT The current detected at the inductor L (iL), the input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 605 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B Connections to circuit 600 are shown.

[0199] In some embodiments, one or more controllers may be used to operate some switches in the circuit, while one or more other controllers may be used to operate other switches in the circuit. For example, a first set of one or more controllers 605 may be operable to control switches S in the front-end stage 610 via a first set of one or more signal lines (e.g., circuit connections) 607. 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C and S 2D The first set of one or more controllers 605 may be operable to control the on / off states and on / off timing of switches S3, S4, and S5 via a second set of one or more signal lines (e.g., circuit connections) 607, thereby controlling the magnetic stage 620 of the circuit. In some embodiments, the first set of one or more controllers 605 may operate the switches S3, S4, and S5 in the front-end stage 610 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 505 may operate the switches S3, S4, and S5. 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C and S 2D For example, the switch S that controls the first stage 1A 、S 1B 、S 1C 、S1D 、S 2A 、S 2B 、S 2C and S 2D The duty cycle of the first set of one or more controllers 605 may depend on the detailed topology and operating mechanism (e.g., slow switching limit vs. fast switching limit). In some embodiments, the first set of one or more controllers 605 may control the switches S of the front-end stage 610 at a duty cycle of approximately 50%. 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C and S 2D In some embodiments, the switch S of the front-end stage 610 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C and S 2D The switches (e.g., S3, S4, S5) of the magnetic stage 620 may be operated independently. In some embodiments, a first set of one or more controllers 605 may receive a first set of one or more feedback / feedforward signals 608, and a second set of one or more controllers 605 may receive a second set of feedback / feedforward signals 608 that may be different from the first set of feedback / feedforward signals 608.

[0200] In some embodiments, the converter can provide two different output voltages. For example, Figure 6B The circuit 640 may include a front-end stage 650 and a magnetic stage 660. The front-end stage 650 may be as previously described. Figure 3A or may be a magnetic based front end stage (e.g. see Figure 9 、 Figure 10 ). The magnetic stage 660 can be configured with an inductor L, a capacitor C B1 and C B2 The first terminal of the buck converter can be connected to any of the following three voltages: V H (e.g., output from front-end stage 650), V IN and common 655 (eg, common ground or 0V). For example, when switch S3 is on and switches S4 and S5 are off, the multi-level buck converter may receive V H (For example, 2*V IN ) input voltage. When switch S4 is turned on and switches S3 and S5 are turned off, the multi-level buck converter can receive VIN When switch S5 is on and switches S3 and S4 are off, the multi-level buck converter can receive an input voltage of 0V. The multi-level buck converter in circuit 640 can also include two output voltage options. For example, the multi-level multi-output buck converter can have capacitors C with different capacitance values. B1 and C B2 , and maintain two different V OUT When switch S6 is on and switch S7 is off, charge can be supplied from the converter to support capacitor C B2 The output voltage V OUT2 When switch S7 is on and switch S6 is off, charge can be supplied from the converter to support capacitor C B1 The output voltage V OUT1 Therefore, the same multi-level buck converter can provide two different output voltages.

[0201] One or more controllers 612 may control switches of the magnetic stages in the circuit 640 (eg, S3, S4, S5, S6, S7) and switches within the front-end stage 650 (eg, see Figure 3A ) to generate the required output voltage V OUT For example, the controller 612 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired output voltage V OUT , as previously described. The controller 612 may be as follows Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 640, there are different signal lines 613 for controlling different switches of the circuit 640, and different feedback / feedforward signal lines 614 for detecting different feedback / feedforward signals (for example, the voltage V OUT1 , voltage V OUT2 , voltage V X , voltage V H , voltage V HI , in V OUT1 The load current sensed at V OUT2 The load current sensed at the inductor L (i L ), input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 612 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B Shown connected to circuit 640.

[0202] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 612 can be operated to control the on / off state and on / off timing of switches in a front-end stage 650 via a first set of one or more signal lines (e.g., circuit connections) 613, thereby controlling the front-end stage 650 (e.g., an SC multiplier stage). A second set of one or more controllers 612 can be operated to control the on / off state and on / off timing of switches S3, S4, and S5 via a second set of one or more signal lines (e.g., circuit connections) 613, thereby controlling the magnetic stage 660 of the circuit. In some embodiments, the first set of one or more controllers 612 can operate the switches in the front-end stage 650 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 612 can operate switches S3, S4, and S5. For example, the duty cycle of controlling the switches of the first stage 650 can depend on the detailed topology and operating mechanism (e.g., slow switching limit vs. fast switching limit). In some embodiments, the first set of one or more controllers 612 can control the switches of the front-end stage 650 at a duty cycle of approximately 50%. In some embodiments, the switches of the front-end stage 650 can operate independently of the switches (e.g., S3, S4, S5) of the magnetic stage 660. In some embodiments, the first set of one or more controllers 612 can receive a first set of one or more feedback / feedforward signals 614, and the second set of one or more controllers 612 can receive a second set of feedback / feedforward signals 614 that can be different from the first set of feedback / feedforward signals 614.

[0203] In some embodiments, the front-end stage 610 (eg, interleaved switched capacitor voltage multiplier) of circuit 600 and the multi-level multi-output buck converter of circuit 650 can be combined. Figure 6C 6 shows a circuit 670 that can have a front-end stage 675 including an interleaved SC voltage doubler and a magnetic stage 685 having a multi-level multi-output buck converter. The front-end stage 675 can be as shown in FIG. Figure 6A The front-end stage 610 operates as described above, and the magnetic stage 685 can be operated as described above with respect to Figure 6B The magnetic stage 660 operates as described.

[0204] One or more controllers 690 may control switches (eg, S 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C 、S2D , S3, S4, S5, S6, S7) to generate the required output voltage V OUT For example, the controller 690 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired output voltage V OUT , as previously described. The controller 690 can be as follows Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 670, there are different signal lines 692 for controlling different switches of the circuit 670, and different feedback / feedforward signal lines 693 for detecting different feedback / feedforward signals (for example, the voltage V OUT1 , voltage V OUT2 , voltage V X , voltage V H 、V OUT1 The current detected at OUT2 The current detected at the inductor L (i L ), input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 690 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B Shown connected to circuit 670.

[0205] In some embodiments, one or more controllers may be used to operate some switches in the circuit, while one or more other controllers may be used to operate other switches in the circuit. For example, a first set of one or more controllers 690 may be operable to control switches S in the front-end stage 675 via a first set of one or more signal lines (e.g., circuit connections) 692. 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C and S 2DThe first set of one or more controllers 690 may be operable to control the on / off states and on / off timing of switches S3, S4, and S5 via a second set of one or more signal lines (e.g., circuit connections) 692, thereby controlling the magnetic stage 685 of the circuit. In some embodiments, the first set of one or more controllers 690 may operate the switches S3, S4, and S5 in the front-end stage 675 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 690 may operate the switches S3, S4, and S5. 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C and S 2D For example, the switch S that controls the first stage 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C and S 2D The duty cycle of the first set of one or more controllers 690 may depend on the detailed topology and operating mechanism (e.g., slow switching limit vs. fast switching limit). In some embodiments, the first set of one or more controllers 690 may control the switches S of the front-end stage 675 at a duty cycle of approximately 50%. 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C and S 2D In some embodiments, the switch S of the front-end stage 675 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C and S 2D The switches (e.g., S3, S4, S5) of the magnetic stage 685 may be operated independently. In some embodiments, a first set of one or more controllers 690 may receive a first set of one or more feedback / feedforward signals 693, and a second set of one or more controllers 690 may receive a second set of feedback / feedforward signals 693 that may be different from the first set of feedback / feedforward signals 693.

[0206] In some embodiments, when V INWhen in the upper part of its range, the above Figures 3A to 6C The voltage V in the front-end stage implementation discussed H may become unnecessarily large. For example, if V IN Supplied by a battery that discharges over time, when the battery is fully charged or nearly fully charged, V H This limitation can be overcome by using a reconfigurable front end (e.g., a reconfigurable switched capacitor converter, a reconfigurable magnetic-based front end) that can convert voltages at multiple conversion ratios and by selecting a voltage that generates a voltage V in the desired range. H The conversion ratio is solved. Figure 7 A circuit 700 is shown that can be used as a reconfigurable switched capacitor front-end stage. The circuit 700 can be used to provide a voltage close to V IN or 0.5*V IN The voltage V T , thus providing close to 2*V depending on the selected operating mode IN or 1.5*V IN One of the voltages V H Voltage V T Then the voltage V H In the previous Figures 3A to 6C The circuit is used in a magnetic stage.

[0207] In circuit 700, when switch S A1 and S A2 Turn on and switch S B When disconnected, capacitors C1 and C2 can be placed in parallel. B Turn on and switch S A1 and S A2 When disconnected, capacitors C1 and C2 can be placed in series. IN The voltage V H When one or more operating modes are used, the switch S A1 and S A2 Can be continuously connected and switch S B can remain open, or the switch S B Can be continuously connected and switch S A1 and S A2 can remain open, and the converter can then be in the first configuration where switch S 1A and S 1B Turn on and switch S 2A and S 2B Disconnect - and the second configuration - where switch S 2A and S 2B Turn on and switch S 1A and S1B Disconnect - Alternate between.

[0208] When it is necessary to provide close to 1.5*V IN The voltage V H One or more operating modes may be used, wherein the converter may switch S B 、S 2A and S 2B Turn on and switch S A1 、S A2 、S 1A and S 1B Disconnected configuration with switch S A1 、S A2 、S 1A and S 1B Turn on and switch S B 、S 2A and S 2B This alternation can provide a IN It charges the series capacitors C1 and C2 and discharges the parallel capacitors C1 and C2 to a voltage V T Although about Figure 7 Describes 2*V IN and 1.5*V IN The voltage of the power supply MOSFET is 0.001V, but the present disclosure is not limited thereto. A person skilled in the art will recognize that by using additional configuration switches and energy transfer capacitors, Figure 7 The reconfigurable converter system architecture 700 can be extended to V IN With V H Between or V IN With V T Providing even more available conversion ratios can provide a greater number of available conversion ratios between V IN The variation of the supplied voltage V H Finer control of

[0209] One or more controllers 705 may control switches (eg, S A1 、S A2 、S B 、S 1A 、S 1B 、S 2A 、S 2B ) to generate the required output voltage V T For example, as previously described, the controller 705 may select (eg, alternate between) switch configurations to synthesize the desired voltage V T . The controller 705 can be as follows Figure 1BThe controller 155 is implemented as described above, but based on the different architecture of the circuit 700, there are different signal lines 707 for controlling different switches of the circuit 700, and different feedback / feedforward signal lines 708 for detecting different feedback / feedforward signals (for example, the voltage V H , voltage V T , voltage V C1 , voltage V VC2 、Input voltage V IN , the current I drawn from the input energy source IN ).

[0210] In some implementations, it may be desirable to utilize a reconfigurable front end and reduce the amount of capacitance required to implement the reconfigurable front end. Figure 8 An example circuit 800 that can be used as an interleaved reconfigurable front end is shown. The circuit 800 may include a first reconfigurable front end circuit 810 and a second reconfigurable front end circuit 820. Such a converter may reduce the voltage used to maintain the voltage V H The total capacitance (for example, reducing capacitor C T Another benefit is that the operations of the first reconfigurable front-end circuit 810 and the second reconfigurable front-end circuit 820 can be combined to achieve a soft "discharge" of the flying capacitor through the magnetic stage, thereby reducing the loss of the reconfigurable front-end circuit. Figure 6A and Figure 6C Similar advantages of interleaved front-ends, but with the added benefit of controlling the voltage V H The circuit 800 may be capable of providing an interleaved front-end converter that can provide close to 2*V resolution depending on the selected operating mode. IN or 1.5*V IN One of the voltages V H The circuit 800 may also be capable of providing interleaved front-end converters that can provide close to 3*V depending on the selected operating mode. IN The voltage V H .

[0211] Using circuit 800, when it is necessary to provide a voltage close to 2*V IN The voltage V H When one or more operating modes are used, the switch S A1 and S A2 Can be continuously turned on (at switch S B disconnected) and the switch S C1 and S C2 Can be continuously turned on (at switch S Ddisconnected) (so that capacitors C1 and C2 are connected in parallel and capacitors C3 and C4 are connected in parallel), or in which switch S B Continuously on (at switch S A1 and S A2 disconnected) and the switch S D Can be continuously turned on (at switch S C1 and S C2 The circuit can then switch on switch S during different parts of the switching cycle of the front end. 1A 、S 1B 、S 1C and S 1D (On switch S 2A 、S 2B 、S 2C and S 2D When disconnected) and connected switch S 2A 、S 2B 、S 2C and S 2D (On switch S 1A 、S 1B 、S 1C and S 1D When it is necessary to provide close to 1.5*V IN The voltage V H One or more operating modes may be used in which the circuit switches on the switch S during different parts of the switching cycle of the front end. B 、S C1 、S C2 、S 2A 、S 2B 、S 2C and S 2D (On switch S A1 、S A2 、S D 、S 1A 、S 1B 、S 1C and S 1D When disconnected) and connected switch S A1 、S A2 、S D 、S 1A 、S 1B 、S 1C and S 1D (On switch S B 、S C1 、S C2 、S 2A 、S 2B 、S 2C and S 2DWhen it is necessary to provide close to 3*V IN The voltage V H One or more operating modes may be used in which the switch S is switched on during different parts of the switching cycle of the circuit front end. A1 、S A2 、S 2A 、S 2B 、S 2C 、S 2D and S D Turn on (at switch S C1 、S C2 、S 1A 、S 1B 、S 1C 、S 1D and S B disconnected) with switch S C1 、S C2 、S 1A 、S 1B 、S 1C 、S 1D and S B Turn on (at switch S A1 、S A2 、S D 、S 2A 、S 2B 、S 2C and S 2D disconnected).

[0212] One or more controllers 805 may provide control signals to switch switches (eg, S A1 、S A2 、S B 、S 1A 、S 1B 、S 1C 、S 1D 、S 2A 、S 2B 、S 2C 、S 2D 、S C1 、S C2 、S D ) is controlled between on and off states to generate the required output voltage V T For example, as previously described, the controller 805 may select (or alternate between) switch configurations to synthesize the desired voltage V T . The controller 805 can be as follows Figure 1BThe controller 155 is implemented as described above, but based on the different architecture of the circuit 800, there are different signal lines 807 for controlling different switches of the circuit 800, and different feedback / feedforward signal lines 808 for detecting different feedback / feedforward signals (for example, the voltage V H , voltage V T , voltage V C1 , voltage V VC2 , voltage V C3 , voltage V C4 、Input voltage V IN , the current I drawn from the input energy source IN ).

[0213] Switched capacitor front-end stage - an example of which is referenced Figures 3A to 8 Described - can only be in V H With V IN The specific ratio is close to the high efficiency, thus limiting the V H An alternative approach could be to use a front-end stage based on magnetic materials, which would allow V H Set to V IN Ideal values ​​are irrelevant. Figure 9 An example of an NRHPZ converter having a magnetic-based front-end stage based on a buck-boost converter is shown in FIG. The circuit 900 includes a first magnetic stage 910, which is a magnetic-based front-end stage. Switches S1, S2 and an energy storage element (e.g., an inductor L) are connected to the circuit. 降压-升压 (L buck-boost )) together form a buck-boost converter to regulate V on capacitor C1 HI and voltage V H In this converter, switches S1 and S2 can operate in a complementary manner, with the duty cycle of S1 being used to set V H Control to be greater than V IN any desired value of V HI Control to V IN Any desired value with the same polarity). As previously mentioned, the second magnetic stage 920 can be implemented with three possible inputs (such as V H 、V IN , 0V) of the 3-level buck converter. That is, the inductor L 降压 (L buck ), capacitor C2 and switches S3 to S5 can operate together as a 3-level buck converter. When switch S3 is turned on and switches S4 and S3 are turned off, the 3-level buck converter can receive V H When switch S4 is turned on and switches S3 and S5 are turned off, the 3-level buck converter can receive V INInput voltage: When switch S5 is on and switches S3 and S4 are off, the 3-level buck converter may receive an input voltage of 0V (eg, the voltage of the common ground 930 ).

[0214] One or more controllers 905 can control the switches (e.g., S1, S2, S3, S4, S5) in the circuit 900 to generate the desired output voltage V OUT For example, the controller 905 may alternate between two switch configurations (for two-phase operation) or three switch configurations (for three-phase operation) to synthesize the desired output voltage V OUT , as described above. The controller 905 can be as follows Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 900, there are different signal lines 907 for controlling different switches of the circuit 900, and different feedback / feedforward signal lines 908 for detecting different feedback / feedforward signals (for example, the voltage V OUT , voltage V X , voltage V H , voltage V HI , in V OUT The load current sensed at the inductor L 降压-升压 The current (i L降压-升压 ), inductor L 降压 The current (i L降压 ), input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 905 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B Controller 1805 or Figure 19 controller 1900 and can be as Figure 18A or Figure 18B Connections to circuit 900 are shown.

[0215] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 905 can be operated to control the on / off state and on / off timing of switches S1 and S2 in a first magnetic stage 910 (e.g., a magnetic front end stage) via a first set of one or more signal lines (e.g., circuit connections) 907, thereby controlling the first magnetic stage 910 (e.g., a magnetic front end stage). A second set of one or more controllers 905 can be operated to control the on / off state and on / off timing of switches S3, S4, and S5 via a second set of one or more signal lines (e.g., circuit connections) 907, thereby controlling a second magnetic stage 920 of the circuit. In some embodiments, the first set of one or more controllers 905 can operate switches S1 and S2 in the first magnetic stage 910 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 905 can operate switches S3, S4, and S5 of the second magnetic stage 920. In some embodiments, switches S1 and S2 of the first magnetic stage 910 can operate independently of switches (e.g., S3, S4, S5) of the second magnetic stage 920. In some embodiments, a first set of one or more controllers 905 can receive a first set of one or more feedback / feedforward signals 908, and a second set of one or more controllers 905 can receive a second set of feedback / feedforward signals 908 that can be different from the first set of feedback / feedforward signals 908.

[0216] In some embodiments, it may be necessary to H The range is chosen to make good use of the voltage ratings of the semiconductor switches in the CMOS process. It may also be necessary to use cascode switches or active clamping techniques or topologies to enable the use of step-down switches when implementing the converter. Figure 10 A circuit 1000 is shown having an NRHPZ converter and using an active clamp structure similar to that of an active neutral point clamp converter. The circuit has a first magnetic stage 1010, which is a magnetic-based front-end stage based on a buck-boost converter. The circuit 1000 may also have a second magnetic stage 1020, which is a 3-level magnetic regulation stage based on a buck converter. Similar to the circuit 900, the first magnetic stage 1010 may allow V H Set to V IN The circuit 1000 can allow the use of a buck switch and actively clamp the switch voltage in the off state. The active clamping structure also allows the inductor L 降压-升压 The voltage across the terminals is actively clamped at zero volts, which is valuable in discontinuous conduction mode. Active clamping of the front-end converter 1010 also allows the inductor L to be 降压-升压Active clamping at both ends of V IN This can be valuable in some situations, including limiting ringing in discontinuous conduction mode operation. IN , in V IN At or below V IN The voltage V HI , the circuit 1000 may only need a rated voltage of V IN A single switch.

[0217] One or more controllers 1005 may control switches (e.g., S1, S2, S3, S4, S5, S6, S7, S8, S9, S100, S110, S120, S130, S140, S150, S160, S170, S180, S190, S200, S210, S220, S320, S420, S520, S 10 、S 11 、S 12 ) to generate the required output voltage V OUT For example, as previously described, the controller 1005 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired output voltage V OUT . The controller 1005 can be as follows Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 1000, there are different signal lines 1007 for controlling different switches of the circuit 1000, and different feedback / feedforward signal lines 1008 for detecting different feedback / feedforward signals (for example, the voltage V OUT , voltage V X , voltage V H , voltage V HI , in V OUT The load current sensed at the inductor L 降压-升压 The current (i L降压-升压 ), inductor L 降压 The current (i L降压 ), input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 1005 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B Connections to circuit 1000 are shown.

[0218] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 1005 can be operated to control the on / off states and on / off timing of switches S1, S2, S3, S4, S5, and S6 in a first magnetic stage 1010 (e.g., a magnetic front end stage) via a first set of one or more signal lines (e.g., circuit connections) 1007, thereby controlling the first magnetic stage 1010 (e.g., a magnetic front end stage). A second set of one or more controllers 1005 can be operated to control switches S7, S8, S9, S10, S11, S12, S13, S14, S15, S16, S17, S18, S19, S20, S21, S22, S3, S4, S5, and S6 via a second set of one or more signal lines (e.g., circuit connections) 1007. 10 、S 11 and S 12 In some embodiments, the first set of one or more controllers 1005 can operate the switches S7, S8, S9, S1020 of the second magnetic stage 1020 in a manner different from that of the second set of one or more controllers 1005. 10 、S 11 and S 12 The switches S1, S2, S3, S4, S5, and S6 in the first magnetic stage 1010 may be operated at a frequency and / or duty cycle of 100 Hz. In some embodiments, the switches S1, S2, S3, S4, S5, and S6 of the first magnetic stage 1010 may be operated independently of the switches (e.g., S7, S8, S9, S10, S11, S12, S13, S14, S15, S16) of the second magnetic stage 1020. 10 、S 11 and S 12 In some embodiments, a first set of one or more controllers 1005 can receive a first set of one or more feedback / feedforward signals 1008, and a second set of one or more controllers 1005 can receive a second set of feedback / feedforward signals 1008 that can be different from the first set of feedback / feedforward signals 1008.

[0219] In some embodiments, a 3-level NRHPZ converter can be implemented without generating a higher DC voltage as shown in FIG. Figures 3A to 10 The V H This may have the added advantage of simplicity compared to the previously discussed approaches. Figure 11 An example of such a converter is shown. Figure 11 The circuit 1100 can be viewed as combining the functions of the first and second magnetic stages discussed previously into one circuit. The circuit 1100 can utilize the flying capacitor C1 to provide a switching voltage level higher than the input voltage. The voltage V of different configurations of switches S1, S2, S3, S4, and S5 is XAs shown in Table 3 below. In Table 3, the “State” column lists various switch configurations of the circuit 1100. A “1” listed in the switch column indicates that the switch is on, and a “0” listed in the switch column indicates that the switch is off. “V X The voltage listed in the " column indicates the V for the five switch configurations shown in the same row. X Output voltage. The "Note" column describes the voltage V across capacitor C1 when the switches in that row are arranged C1 situation.

[0220] Table 3

[0221]

[0222] By modulating between the switching states shown in Table 3 above (e.g., 2 states per switching cycle, or 3 states per switching cycle for three-phase operation), V X The local average value of V Y The desired local average is generated at . Then, the voltage V Y Can be used as output V OUT (e.g. in the case of capacitor filter C2), or for having a circuit that guides i between multiple outputs L The additional switch in the single-input multiple-output (SIMO) system. The voltage V X Can be in V IN State and 2*V IN modulates between states to provide the desired average voltage V Y >V IN Voltage V X You can also use V IN The modulation is performed between the state and the 0V state to synthesize the required average voltage V Y <V IN Three-phase control can be used to achieve close to V IN The voltage V Y Other methods such as 2*V IN Modulation between the state and the 0V state can also be used to achieve a voltage close to V IN The voltage V Y State E can be used to make V X momentarily approaches zero (e.g., has a magnitude less than V IN 10% of the nature).

[0223] One or more controllers 1105 can control the switches (e.g., S1, S2, S3, S4, S5) in the circuit 1100 to generate a desired average voltage V Y Or output voltage V OUTFor example, as previously described, the controller 1105 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired average voltage V Y Or output voltage V OUT . The controller 1105 can be as follows Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 1100, there are different signal lines 1107 for controlling different switches of the circuit 1100, and different feedback / feedforward signal lines 1108 for detecting different feedback / feedforward signals (for example, the voltage V OUT , voltage V X , voltage V Y , voltage V C , in V OUT The load current sensed at the inductor L (i L ), input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 1105 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B Connections to circuit 1100 are shown.

[0224] Those skilled in the art will recognize that other topologies can be implemented that also produce the desired switching levels. Figure 12 One or more controllers 1205 can control the switches (e.g., S1, S2, S3, S4, S5) in the circuit 1200 to generate a desired average voltage V Y Or output voltage V OUT For example, as previously described, the controller 1205 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired average voltage V Y Or output voltage V OUT . The controller 1205 can be as follows Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 1200, there are different signal lines 1207 for controlling different switches of the system architecture 1200, and different feedback / feedforward signal lines 1208 for detecting different feedback / feedforward signals (e.g., voltage V OUT , voltage V X , average voltage V Y , voltage V C1 , in V OUTThe load current sensed at the inductor L (i L ), input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 1205 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1800 and can be as Figure 18A or Figure 18B 1205 is shown connected to the system architecture.

[0225] Although about Figures 9 to 12 The described circuit may have the advantage of simplicity, but due to the time limit of charge transfer to the flying capacitor C1, the result is close to 2*V IN This problem can be solved by using an interleaved version of the circuit, in which the two flying capacitors are connected alternately to synthesize a voltage higher than V IN The voltage V X . Figure 13 The circuit 1300 shown is one of the converters that can realize this function. In the circuit 1300, switches S1 and S 1A 、S 1B , S2, S 2A and S 2B The rated voltage is V IN Switch S M1 and S M2 Can be rated for + / -V IN (Bidirectional blocking). Switch S M3 Can be rated at 2*V IN Switch S M3 It can also be implemented as a series connection of lower voltage switches or as a clamp to allow V IN 3 switch structure.

[0226] Switches S1, S 1A 、S 1B , S2, S 2A 、S 2B 、S M1 、S M2 and S M3 The voltage V of different configurations X As shown in Table 4 below. In Table 4, the "State" column lists various switch configurations of the circuit 1300. The "Switch On" column lists the switches in a row that are on. Switches that are not listed as on can be considered off in this state. "V X ” column indicates the voltage V for the switch configuration shown in the same row X Output.

[0227] Table 4

[0228] state On switch <![CDATA[Voltage (V) at Node 1319 X )]]> 1 <![CDATA[S 1A ,S 1B ,S 2A ,S 2B ,S M3 ]]> 0 2 <![CDATA[S 1A ,S 1B ,S 2A ,S 2B ,S M1 ,S M2 ]]> <![CDATA[V IN ]]> 3 <![CDATA[S1,S 2A ,S 2B ,S M1 ]]> <![CDATA[V IN +V C1 ≈2*V IN ]]> 4 <![CDATA[S 1A ,S 1B ,S2,S M2 ]]> <![CDATA[V IN +V C2 ≈2*V IN ]]>

[0229] In order to synthesize a value higher than V IN The converter can switch between state 3 and state 2 in the first cycle and between state 4 and state 2 in the second cycle, alternating between the first cycle and the second cycle. IN The converter can switch between state 2 and state 1 in each cycle. IN To output a voltage of 1, the converter may use three-phase switching between states 2, 3, and 1 in the first cycle and between states 2, 4, and 1 in the second cycle, and alternate between the first cycle and the second cycle.

[0230] One or more controllers 1305 may control switches (eg, S 1A 、S 1B , S1, S 2A 、S 2B , S2, S M1 、S M2 、S M3 ) to generate the required average voltage V Y Or output voltage V OUT For example, as previously described, the controller 1305 may alternate between two switching configurations (for two-phase operation) or three switching configurations (for three-phase operation) to synthesize the desired average voltage V Y Or output voltage V OUT Controller 1305 can be as follows. Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 1300, there are different signal lines 1307 for controlling different switches of the circuit 1300, and different feedback / feedforward signal lines 1308 for detecting different feedback / feedforward signals (for example, the voltage V OUT , voltage V X , average voltage V Y , voltage V C1 , voltage V C2 , in V OUT The load current sensed at the inductor L (i L ), input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 1305 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18BConnections to circuit 1300 are shown. have Multi-output architecture of NRHPZ converter circuit

[0231] In a discrete power modulation system, multiple voltages (such as V A 、V B 、V C ...) (e.g. using a multi-output power generator), the power modulator can select the required input voltage from these voltages. There are many ways to achieve multi-voltage output through NRHPZ conversion. One method can be to use a SIMO converter based on the NRHPZ structure to generate two or more levels, such as Figure 6B and Figure 6C Given two outputs, such as Figure 6B and Figure 6C As shown, additional outputs can be generated using switched capacitor converters or differential switched capacitor converters connected to one or both of these outputs.

[0232] Another way to synthesize multiple outputs could be to use two or more NRHPZ converters, including Figure 2A 、 Figure 2B or Figure 2C Any configuration suggested in . Figure 14A and Figure 14B Examples of circuits 1400 and 1450 are shown, respectively, each of which includes two NRHPZ converters. Figure 14A The circuit 1400 includes a NRHPZ converter 1410 and a NRHPZ converter 1420, both of which are connected to a voltage source V IN and a common ground 1430. A switched capacitor (SC) stage 1440 can be connected to the outputs of both NRHPZ converters 1410 and 1420 and can be used to generate additional outputs based on the outputs of the NRHPZ converters. SC stage 1440 can also optionally have a common ground with NRHPZ converters 1410 and 1420. For example, SC stage 1440 can be implemented using a common reference or differential SC converter structure. In some embodiments, one or more additional NRHPZ converters can be introduced into the architecture to generate more voltage outputs.

[0233] One or more controllers 1405 can control the switches in the NRHPZ converters 1410, 1420 and the SC stage 1440 in the circuit 1400 to generate the desired output voltage V A 、V B and V CFor example, as previously described, the controller 1405 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired output voltage V A 、V B and / or V C Controller 1405 can be as follows Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 1400, there are different signal lines 1407 for controlling different switches of the circuit 1400, and different feedback / feedforward signal lines 1408 for detecting different feedback / feedforward signals (for example, the voltage V A , voltage V B , voltage V C Voltage V IN , in V A The load current sensed at V B The load current sensed at V C The current of the load sensed at , the current of the inductor (in the NRHPZ converters 1410, 1420), the voltage level maintained by the capacitor in the SC stage 1440, the current I drawn from the input energy source IN In some embodiments, the controller 1405 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B Connections to circuit 1400 are shown.

[0234] In some embodiments, one or more controllers may be used to operate some switches in a circuit, while one or more other controllers may be used to operate other switches in the circuit. For example, a first set of one or more controllers 1405 may be operable to control the on / off state and on / off timing of switches in an NRHPZ converter 1410 via a first set of one or more signal lines (e.g., circuit connections) 1407, thereby controlling NRHPZ converter 1410. A second set of one or more controllers 1405 may be operable to control the on / off state and on / off timing of switches in an NRHPZ converter 1420 via a second set of one or more signal lines (e.g., circuit connections) 1407, thereby controlling NRHPZ converter 1420. A third set of one or more controllers 1405 may be operable to control the on / off state and / or on / off timing of switches in an SC converter 1440 via a third set of one or more signal lines (e.g., circuit connections) 1407, thereby controlling SC converter 1440. In some embodiments, the first set of one or more controllers 1405 can operate the switches in the NRHPZ converter 1410 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 1405 can operate the switches in the NRHPZ converter 1420 and / or at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the third set of one or more controllers 1405 can operate the switches in the SC converter 1440. In some embodiments, the third set of one or more controllers 1405 can operate the switches in the SC converter 1450 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the first set of one or more controllers 1405 can operate the switches in the NRHPZ converter 1410 and / or at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 1405 can operate the switches in the NRHPZ converter 1420. For example, the duty cycle at which the switches in the SC converter 1440 are operated can depend on the detailed topology and operating mechanism (e.g., slow switching limit versus fast switching limit). In some embodiments, the third set of one or more controllers 1405 can control the switches of the SC converter 1440 at a duty cycle of approximately 50%. In some embodiments, the switches of the NRHPZ converter 1410 can be operated independently of the switches of the NRHPZ converter 1420 and / or the SC converter 1440. In some embodiments, the switches of the SC converter 1440 can be operated independently of the switches of the NRHPZ converter 1410 and / or the NRHPZ converter 1420.In some embodiments, a first group of one or more controllers 1405 may receive a first group of one or more feedback / feedforward signals 1408, a second group of one or more controllers 1405 may receive a second group of feedback / feedforward signals 1408 that may be different from the first group of feedback / feedforward signals 1408, and a third group of one or more controllers 1405 may receive a third group of feedback / feedforward signals 1408 that is different from the first and second groups of feedback / feedforward signals 1408.

[0235] Figure 14B The circuit 1450 includes a NRHPZ converter 1460 and a NRHPZ converter 1470, both of which are connected to a voltage source V IN and a common ground 1480. As shown, the two NRHPZ converters 1460 and 1470 can be connected in a cascade interconnection. The SC stage 1485 can be connected to the voltage outputs (e.g., V A 、V B ) and can be used to generate additional voltage outputs (e.g., V C ,……,V Z SC stage 1485 may also optionally share a common ground with NRHPZ converters 1460, 1470. For example, SC stage 1485 may be implemented using a common reference or differential SC converter structure. In some embodiments, one or more additional NRHPZ converters may be incorporated into the circuit to generate more voltage outputs.

[0236] One or more controllers 1455 can control the switches in the NRHPZ converters 1460, 1470 and the SC stage 1485 in the circuit 1450 to produce the desired output voltage V A 、V B and V C For example, as previously described, the controller 1455 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired output voltage V A 、V B and / or V C . The controller 1455 can be as follows Figure 1B The controller 155 is implemented as described above, but based on the different architecture of the circuit 1450, it has different signal lines 1466 for controlling different switches of the circuit 1400 and different feedback / feedforward signal lines 1467 for detecting different feedback / feedforward signals (e.g., voltage V A , voltage V B , voltage V C , voltage VIN 、V A The load current sensed at V B The load current sensed at V C The current of the load sensed at , the current of the inductor (in the NRHPZ converters 1460, 1470), the voltage level maintained by the capacitor in the SC stage 1485, the current I drawn from the input energy source IN In some embodiments, the controller 1455 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B Connected to circuit 1450 as shown.

[0237] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 1455 can be operated to control the on / off state and on / off timing of switches in NRHPZ converter 1460 via a first set of one or more signal lines (e.g., circuit connections) 1466, thereby controlling NRHPZ converter 1460. A second set of one or more controllers 1455 can be operated to control the on / off state and on / off timing of switches in NRHPZ converter 1470 via a second set of one or more signal lines (e.g., circuit connections) 1466, thereby controlling NRHPZ converter 1470. A third set of one or more controllers 1405 can be operated to control the on / off state and / or on / off timing of switches in SC converter 1485 via a third set of one or more signal lines (e.g., circuit connections) 1466, thereby controlling SC converter 1440. In some embodiments, the first set of one or more controllers 1455 can operate the switches in the NRHPZ converter 1460 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 1455 can operate the switches in the NRHPZ converter 1470 and / or at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the third set of one or more controllers 1455 can operate the switches in the SC converter 1485. In some embodiments, the third set of one or more controllers 1455 can operate the switches in the SC converter 1485 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the first set of one or more controllers 1455 can operate the switches in the NRHPZ converter 1460 and / or at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 1455 can operate the switches in the NRHPZ converter 1470. For example, the duty cycle at which the switches in the SC converter 1485 are operated can depend on the detailed topology and operating mechanism (e.g., slow switching limit versus fast switching limit). In some embodiments, the third set of one or more controllers 1455 can control the switching of the SC converter 1485 at a duty cycle of approximately 50%. In some embodiments, the switching of the NRHPZ converter 1460 can be operated independently of the switching of the NRHPZ converter 1470 and / or the SC converter 1485. In some embodiments, the switching of the SC converter 1485 can be operated independently of the switching of the NRHPZ converter 1460 and / or the NRHPZ converter 1470.In some embodiments, a first group of one or more controllers 1455 may receive a first group of one or more feedback / feedforward signals 1467, a second group of one or more controllers 1455 may receive a second group of feedback / feedforward signals 1467 that may be different from the first group of feedback / feedforward signals 1467, and a third group of one or more controllers 1455 may receive a third group of feedback / feedforward signals 1467 that is different from the first and second groups of feedback / feedforward signals 1467.

[0238] In some embodiments, circuit blocks can be shared to generate a multi-output NRHPZ converter. For example, a 3-level NRHPZ converter can use a front-end stage (e.g., a boost stage) to generate V IN Additional voltage levels above, such as Figures 3A to 10 This front-end stage can be shared with multiple 2-level and / or 3-level magnetic conversion stages to generate multiple outputs. Figure 15 An example of this implementation is shown in . Figure 15 In the circuit 1500, additional voltage outputs can be generated using a switched capacitor (SC) conversion stage 1550 fed from one or two outputs and / or a common ground of a multi-output converter or by using an additional three-level magnetic conversion stage fed from the same front-end stage. For example, the circuit 1500 may include a front-end stage (magnetic or switched capacitor boost stage) 1510 that charges the capacitor C1. The circuit 1500 may also include two 3-level magnetic stages (e.g., 3-level buck converters) 1520, 1540 connected to the front-end stage 1510, with the 3-level magnetic stage 1520 outputting a voltage V A , and the 3-level magnetic stage 1540 output voltage V B The circuit 1500 may further include a circuit connected to the output voltage V A and / or V B The switched capacitor converter stage 1550 outputs another voltage (eg, V C ,...,V Z SC converter stage 1550 may also optionally have a common ground (e.g., ground 1560) with NRHPZ converters 1520, 1540 (e.g., ground 1530). For example, SC stage 1485 may be implemented with a common reference or differential SC converter structure. In some embodiments, one or more additional NRHPZ converters may be introduced into the circuit to generate even more voltage outputs.

[0239] One or more controllers 1505 can control switches (e.g., S1, S2, S3, S4, S5, S6) and switches in the boost stage 1510 and SC converter stage 1550 in the circuit 1500 to generate a desired output voltage V A 、V B 、VC For example, as previously described, the controller 1505 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired output voltage V A 、V B and / or V C . The controller 1505 can be as follows Figure 1B The controller 155 is implemented as described in the embodiment of the present invention, but based on the different architecture of the circuit 1500, it has different signal lines 1507 for controlling different switches of the circuit 1500 and different feedback / feedforward signal lines 1508 for detecting different feedback / feedforward signals (for example, the voltage V A , voltage V B , voltage V C , voltage V HI , the voltage of the capacitor or inductor in the boost stage 1510, the voltage of the capacitor in the SC converter stage 1550, the voltage of the capacitor in the V A The load current sensed at V B The load current sensed at V C The load current sensed at the input, the current of the inductor L1, the current of the inductor L2, the input voltage V IN , the current I drawn from the input energy source IN In some embodiments, the controller 1505 may include a feed-forward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B Connections to circuit 1500 are shown.

[0240] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 1505 can be operated to control the on / off state and on / off timing of a switch front-end stage 1510 via a first set of one or more signal lines (e.g., circuit connections) 1507, thereby controlling the front-end stage 1510. A second set of one or more controllers 1505 can be operated to control the on / off state and on / off timing of switches in a 3-level magnetic stage 1520 via a second set of one or more signal lines (e.g., circuit connections) 1507, thereby controlling the 3-level magnetic stage 1520. A third set of one or more controllers 1505 can be operated to control the on / off state and / or on / off timing of switches in a 3-level magnetic stage 1540 via a third set of one or more signal lines (e.g., circuit connections) 1507, thereby controlling the 3-level magnetic stage 1540. The fourth set of one or more controllers 1505 may be operable to control the on / off states and / or on / off timing of switches in the SC converter stage 1550 , thereby controlling the SC converter stage 1550 .

[0241] In some embodiments, the first set of one or more controllers 1505 can operate switches in the front-end stage 1510 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 1505 can operate switches in the 3-level magnetic stage 1520 and / or different from the frequency and / or duty cycle at which the third set of one or more controllers 1505 can operate switches in the 3-level magnetic stage 1540 and / or different from the frequency and / or duty cycle at which the fourth set of one or more controllers 1505 can operate switches in the SC converter stage 1550. In some embodiments, the fourth set of one or more controllers 1505 can operate the switches in the SC converter 1550 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the first set of one or more controllers 1505 can operate the switches in the front-end stage 1510, the frequency and / or duty cycle at which the second set of one or more controllers 1505 can operate the switches in the 3-level magnetic stage 1520, and / or the frequency and / or duty cycle at which the third set of one or more controllers 1505 can operate the switches in the 3-level magnetic stage 1540. For example, the duty cycle at which the switches in the front-end stage 1510 and / or the SC converter stage 1550 operate can depend on the detailed topology and operating mechanism (e.g., slow switching limit versus fast switching limit). In some embodiments, the first set of one or more controllers 1505 can control the switches in the front-end stage 1510 at a duty cycle of approximately 50%. In some embodiments, the fourth set of one or more controllers 1505 can control the switches in the SC converter 1550 at a duty cycle of approximately 50%. In some embodiments, the second set of one or more controllers can operate switches in the 3-level magnetic stage 1520 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the third set of one or more controllers can operate switches in the 3-level magnetic stage 1540.

[0242] In some embodiments, the switches of the front-end stage 1510 can be operated independently of the switches of the 3-level magnetic stage 1520, the 3-level magnetic stage 1540, and / or the SC converter 1550. In some embodiments, the switches of the SC converter 1550 can be operated independently of the switches of the front-end stage 1510, the 3-level magnetic stage 1520, and the 3-level magnetic stage 1540. In some embodiments, the switches of the 3-level magnetic stage 1520 can be operated independently of the switches of the 3-level magnetic stage 1540. In some embodiments, a first group of one or more controllers 1505 may receive a first group of one or more feedback / feedforward signals 1508, a second group of one or more controllers 1505 may receive a second group of feedback / feedforward signals 1508 that may be different from the first group of feedback / feedforward signals 1508, a third group of one or more controllers 1505 may receive a third group of feedback / feedforward signals 1508 that is different from the first and second groups of feedback / feedforward signals 1508, and a fourth group of one or more controllers 1505 may receive a fourth group of feedback / feedforward signals 1508 that is different from the first, second, and third groups of feedback / feedforward signals 1508.

[0243] Figure 16A and Figure 16B Each shows Figure 14A In each case, the buck converter is shown as an example NRHPZ converter. However, one of ordinary skill in the art will recognize that one or both of the buck converters shown in each of these examples may be replaced with a three-level buck converter as previously described herein, or may be implemented as a three-level buck converter with a shared front end, such as Figure 15 As shown in .

[0244] Figure 16A An example circuit 1600 is shown in which an output voltage V3 can be achieved using an SC converter 1610 fed from a voltage V1, thereby generating a voltage level V3 of V1 + V2. The circuit 1600 may include two NRHPZ converters 1620, 1630 (here, buck converters). The NRHPZ converter 1620 may output a voltage V1. The NRHPZ converter 1630 may output a voltage V2. When the switch S 5A and S 5B Turn on and switch S 6A and S 6B When disconnected, the flying capacitor C f can be charged to voltage V1. Then, when switch S 6A and S 6B When conducting, capacitor C1 can fThe voltage on V1 is charged to the voltage V1, thereby generating a voltage V3 of V1 + V2 (eg, V1 + V2 = V3).

[0245] One or more controllers 1605 may control switches (e.g., S1, S2, S3, S4, S5, S6, S7, S8, S9, S10, S11, S12, S13, S14, S15, S16, S17, S18, S19, S20, S21, S32, S43, S54, S65, S76, S87, S9, S10, S1 5A 、S 5B 、S 6A 、S 6B ) to generate the desired output voltages V1, V2, V3. For example, the controller 1605 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired output voltages V1, V2, and / or V3, as previously discussed. The controller 1605 may be configured as described for Figure 1B The controller 155 is implemented as described above, but based on a different architecture of the circuit 1600, has different signal lines 1607 for controlling different switches of the circuit 1600, and has different signal lines 1607 for detecting different feedback / feedforward signals (e.g., voltage V1, voltage V2, voltage V3, voltage of capacitor C1, voltage of capacitor C2, voltage of capacitor C3, voltage of capacitor C f The voltage of the inductor L1, the current in the inductor L2, the current to the load at voltage V1, the current to the load at voltage V2, the current to the load at voltage V3, the input voltage V IN , the current I drawn from the input energy source IN ) of different feedback / feedforward signal lines 1608. In some embodiments, the controller 1605 may include a feedforward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B 16. The circuit 1600 is shown connected thereto.

[0246] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 1605 can be operated to control the on / off state and on / off timing of switches in NRHPZ converter 1620 via a first set of one or more signal lines (e.g., circuit connections) 1607, thereby controlling NRHPZ converter 1620. A second set of one or more controllers 1605 can be operated to control the on / off state and on / off timing of switches in NRHPZ converter 1630 via a second set of one or more signal lines (e.g., circuit connections) 1607, thereby controlling NRHPZ converter 1630. A third set of one or more controllers 1605 can be operated to control the on / off state and / or on / off timing of switches in SC converter 1610 via a third set of one or more signal lines (e.g., circuit connections) 1607, thereby controlling SC converter 1610. In some embodiments, the first set of one or more controllers 105 can operate the switches in the NRHPZ converter 1620 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 1605 can operate the switches in the NRHPZ converter 1630 and / or the frequency and / or duty cycle at which the third set of one or more controllers 1605 can operate the switches in the SC converter 1610. In some embodiments, the third set of one or more controllers 1605 can operate the switches in the SC converter 1610 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the first set of one or more controllers 1605 can operate the switches in the NRHPZ converter 1620 and / or the frequency and / or duty cycle at which the second set of one or more controllers 1605 can operate the switches in the NRHPZ converter 1630. For example, the duty cycle at which the switches in SC converter 1610 operate can depend on the detailed topology and operating mechanism (e.g., slow switching limit versus fast switching limit). In some embodiments, the third set of one or more controllers 1605 can control the switches in SC converter 1610 at a duty cycle of approximately 50%. In some embodiments, the switches in NRHPZ converter 1620 can operate independently of the switches in NRHPZ converter 1630 and / or SC converter 1610. In some embodiments, the switches in SC converter 1610 can operate independently of the switches in NRHPZ converter 1620 and / or NRHPZ converter 1630.In some embodiments, a first group of one or more controllers 1605 may receive a first group of one or more feedback / feedforward signals 1608, a second group of one or more controllers 1605 may receive a second group of feedback / feedforward signals 1608 that may be different from the first group of feedback / feedforward signals 1608, and a third group of one or more controllers 1605 may receive a third group of feedback / feedforward signals 1608 that is different from the first and second groups of feedback / feedforward signals 1608.

[0247] Figure 16B An example circuit 1650 is shown in which voltage V3 can be achieved by a switched capacitor converter stage 1670 that is differentially fed between V1 and V2, thereby generating a voltage V3 that is V2+(V2-V1) or 2*V2-V1. Circuit 1650 may include two NRHPZ converters 1660, 1680 (here, buck converters). NRHPZ converter 1660 may output voltage V1. NRHPZ converter 1680 may output voltage V2. When switch S 5A and S 5B Turn on and switch S 6A and S 6B When disconnected, the capacitor C f Can be charged to voltage V2-V1. When switch S 6A and S 6B Turn on and switch S 5A and S 5B When disconnected, capacitor C1 can be f The voltage on the capacitor C1 is charged to V2-V1. The voltage V2-V1 on the capacitor C1 and the voltage V2 are then connected, which can generate a voltage V3 of V2+V2-V1 (for example, V2+V2-V1=V3 or 2*V2-V1=V3).

[0248] One or more controllers 1655 can control switches (e.g., S1, S2, S3, S4, S5) in circuit 1650. 5A 、S 5B 、S 6A 、S 6B ) to generate the desired output voltages V1, V2, V3. For example, the controller 1655 may alternate between two switch configurations (for two-phase operation) or three switch configurations (for three-phase operation) to synthesize the desired output voltages V1, V2, and / or V3, as previously discussed. The controller 1655 may be configured as described for Figure 1BThe controller 155 is implemented as described above, but based on a different architecture of the circuit 1650, with different signal lines 1657 for controlling different switches of the circuit 1650, and with different signal lines 1657 for detecting different feedback / feedforward signals (e.g., voltage V1, voltage V2, voltage V3, voltage of capacitor C1, voltage of capacitor C2, voltage of capacitor C3, voltage of capacitor C f The voltage of the inductor L1, the current in the inductor L2, the current to the load at voltage V1, the current to the load at voltage V2, the current to the load at voltage V3, the input voltage V IN , the current I drawn from the input energy source IN ) of different feedback / feedforward signal lines 1658. In some embodiments, the controller 1655 may include a feedforward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B 16. The circuit 1650 is shown connected to FIG.

[0249] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 1655 can be operated to control the on / off state and on / off timing of switches in an NRHPZ converter 1660 via a first set of one or more signal lines (e.g., circuit connections) 1657, thereby controlling NRHPZ converter 1660. A second set of one or more controllers 1655 can be operated to control the on / off state and on / off timing of switches in an NRHPZ converter 1680 via a second set of one or more signal lines (e.g., circuit connections) 1657, thereby controlling NRHPZ converter 1680. A third set of one or more controllers 1655 can be operated to control the on / off state and / or on / off timing of switches in an SC converter 1670 via a third set of one or more signal lines (e.g., circuit connections) 1657, thereby controlling SC converter 1670. In some embodiments, the first set of one or more controllers 1655 can operate the switches in the NRHPZ converter 1660 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 1655 can operate the switches in the NRHPZ converter 1680 and / or the frequency and / or duty cycle at which the third set of one or more controllers 1655 can operate the switches in the SC converter 1670. In some embodiments, the third set of one or more controllers 1655 can operate the switches in the SC converter 1670 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the first set of one or more controllers 1655 can operate the switches in the NRHPZ converter 1660 and / or the frequency and / or duty cycle at which the second set of one or more controllers 1655 can operate the switches in the NRHPZ converter 1680. For example, the duty cycle at which the switches in SC converter 1670 operate can depend on the detailed topology and operating mechanism (e.g., slow switching limit versus fast switching limit). In some embodiments, the third set of one or more controllers 1655 can control the switches of SC converter 1670 at a duty cycle of approximately 50%. In some embodiments, the switches of NRHPZ converter 1660 can be operated independently of the switches of NRHPZ converter 1680 and / or SC converter 1670. In some embodiments, the switches of SC converter 1670 can be operated independently of the switches of NRHPZ converter 1660 and / or NRHPZ converter 1680.In some embodiments, a first group of one or more controllers 1655 may receive a first group of one or more feedback / feedforward signals 1658, a second group of one or more controllers 1655 may receive a second group of feedback / feedforward signals 1658 that may be different from the first group of feedback / feedforward signals 1658, and a third group of one or more controllers 1655 may receive a third group of feedback / feedforward signals 1658 that is different from the first and second groups of feedback / feedforward signals 1658.

[0250] It can be recognized that although Figure 16A and Figure 16B The two NRHPZ converters are shown as IN are fed in parallel through their inputs, but either implementation ( Figure 16A or Figure 16B can be realized by connecting two NRHPZ converters in cascade, as shown in Figure 14B Likewise, although example switched capacitor converters (e.g., 1610, 1670) are shown, one of ordinary skill in the art will recognize that interleaved switched capacitor converters may be used instead, such as with respect to Figure 6A 、 Figure 6C or Figure 8 Those described.

[0251] Figure 17A The use of a single NRHPZ converter 1720 together with a multi-output switched capacitor converter 1730 to synthesize multiple levels of output voltage (eg, V1 . . . V N ) of the example circuit 1700. One or more controllers 1705 can control the switches in the NRHPZ converter 1720 and / or the switched capacitor converter 1730 in the circuit 1700 to generate the desired output voltage V1 ... V N For example, the controller 1705 may alternate between two switching configurations (for two-phase operation) or three switching configurations (for three-phase operation) to synthesize the desired output voltages V1…V N , as previously discussed. The controller 1705 may be configured as for Figure 1B The controller 155 is implemented as described above, but based on a different architecture of the circuit 1700, with different signal lines 1707 for controlling different switches of the circuit 1700, and with different signal lines 1707 for detecting different feedback / feedforward signals (e.g., V1 ... V N The voltage at V1…V NThe current to the load at the NRHPZ converter 1720, the voltage and / or current at the output of the NRHPZ converter 1720, the voltage on the capacitor in the NRHPZ converter 1720 or the SC converter 1730, the current in the inductor in the NRHPZ 1720, the input voltage V IN , the current I drawn from the input energy source IN ) of different feedback / feedforward signal lines 1708. In some embodiments, the controller 1705 may include a feedforward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B is connected to circuit 1700 as shown in FIG. Figure 17A It is not explicitly shown, but it should be understood that the switched capacitor converter 1730 may additionally or alternatively be connected to the input voltage V directly or via a switch connection. IN , so that the switched capacitor converter 1730 can be fed between the output of the NRHPZ converter 1720 and ground, or between the output of the NRHPZ converter 1720 and V IN are fed differentially between them.

[0252] In some embodiments, one or more controllers can be used to operate some switches in the circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 1705 can be operated to control the on / off state and on / off timing of switches in NRHPZ converter 1720 via a first set of one or more signal lines (e.g., circuit connections) 1707, thereby controlling NRHPZ converter 1720. A second set of one or more controllers 1705 can be operated to control the on / off state and on / off timing of switches in SC converter 1730 via a second set of one or more signal lines (e.g., circuit connections) 1707, thereby controlling SC converter 1730. In some embodiments, the first set of one or more controllers 1705 can operate the switches in the NRHPZ converter 1720 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 1705 can operate the switches in the SC converter 1730. For example, the duty cycle at which the switches in the SC converter 1730 operate can depend on the detailed topology and operating mechanism (e.g., slow switching limit vs. fast switching limit). In some embodiments, the third set of one or more controllers 1705 can control the switches of the SC converter 1730 at a duty cycle of approximately 50%. In some embodiments, the switches of the NRHPZ converter 1720 can operate independently of the switches of the SC converter 1730. In some embodiments, a first set of one or more controllers 1705 may receive a first set of one or more feedback / feedforward signals 1708, and a second set of one or more controllers 1705 may receive a second set of feedback / feedforward signals 1708 that may be different from the first set of feedback / feedforward signals 1708.

[0253] Figure 17B shows that it is possible to achieve much higher input voltage V IN Example circuit 1730 of an output voltage of 1730. For example, circuit 1730 may be capable of synthesizing up to 3*V IN The circuit 1730 may include a single NRHPZ converter 1755 having a front-end stage 1740 (shown here as a switched capacitor front-end stage) and a multiple output switched capacitor converter 1760. As previously described with respect to Figure 3A As discussed, the NRHPZ converter 1755 can select three voltage levels (e.g., V H =V HI +V IN 、V IN , ground or 0V) as the input of its 3-level buck converter. Figure 3AAs discussed, one or more controllers (here controller 1732) can use two-phase or three-phase operation at different V H =V HI +V IN 、V IN The multi-output switched capacitor converter 1760 can then generate various possible output voltages (e.g., V1, V2, V3) based on the voltage V2 output from the NRHPZ converter 1755. For example, by operating the switched capacitor converter 1760, each of C2 and C3 will maintain a voltage up to 0.5*V2. When the switch S 1A 、S 1B 、S 1C 、S 1D 、S 1E and S 1F Turn on and switch S 2A 、S 2B 、S 2C 、S 2D 、S 2E and S 2F When disconnected, the capacitor C f3 Can be charged to a voltage up to 0.5*V2 (V2-0.5*V2 (the voltage on capacitor C3)), capacitor C f4 can be charged to a voltage up to 0.5*V2 (V2-0.5*V2 (the voltage on capacitor C3)), and capacitor C f5 It can be charged to a voltage up to 0.5*V2 (the voltage on capacitor C3). Then, when switch S 2A 、S 2B 、S 2C 、S 2D 、S 2E and S 2F Turn on and switch S 1A 、S 1B 、S 1C 、S 1D 、S 1E and S 1F When disconnected, capacitors C3 and C f4 and C f5 Can be connected to produce a voltage up to 1.5*V2, and can charge capacitor C1 to up to 0.5*V2 (1.5*V2-V2 at the V2 rail). With C1, C2, and C3 each maintaining a voltage up to 0.5*V2, V3 can output a voltage up to 1.5*V2. V2 can have a voltage up to 2*V IN The voltage (see e.g. Figure 3AThus, circuit 1730 can generate up to 1.5*2*V IN or 3*V IN The maximum output voltage. When the switch S 1A 、S 1B 、S 1C 、S 1D 、S 1E and S 1F Turn on again and switch S 2A 、S 2B 、S 2C 、S 2D 、S 2E and S 2F When disconnected again, capacitors C3 and C f2 and C f3 will be connected, which can keep the charged capacitor C1 at a voltage up to 0.5*V2 and maintain the output voltage V3 at 3*V IN Therefore, by controlling the switch S 1A 、S 1B 、S 1C 、S 1D 、S 1E 、S 1F 、S 2A 、S 2B 、S 2C 、S 2D 、S 2E and S 2F The on / off state can synthesize 0V and 3*V IN Multiple voltages in between.

[0254] Able to support 2*V IN The maximum output of the design can be achieved by supplying the voltage at the V3 rail (not shown) instead of at the V2 rail (as shown in FIG. Figure 17B ) is fed to the switched capacitor converter 1760. In some embodiments, the multi-output switched capacitor converter 1760 can optionally be selectively fed at different voltage rails by introducing additional selector switches (not shown), thereby achieving greater reconfigurability.

[0255] One or more controllers 1732 may control switches (eg, S A1 、S A2 、S B1 、S B2 , S3, S4, S5, S 1A 、S 1B 、S 1C 、S 1D 、S 1E 、S1F 、S 2A 、S 2B 、S 2C 、S 2D 、S 2E 、S 2F ) and optionally additional selector switches to generate the desired output voltages V1, V2, V3. For example, the controller 1732 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired output voltages V1, V2, and / or V3, as previously discussed. The controller 1732 may be configured as described for Figure 1B The controller 155 is implemented as described above, but based on a different architecture of the circuit 1730, with different signal lines 1734 for controlling different switches of the circuit 1730, and with different signal lines 1734 for detecting different feedback / feedforward signals (e.g., voltage V1, voltage V2, voltage V3, capacitors (e.g., C1, C2, C3, C HI 、C f1 、C f2 、C f3 、C f4 、C f5 ) voltage, the current of the inductor L (for example, i L ), the current to the load at voltage V1, the current to the load at voltage V2, the current to the load at voltage V3, the input voltage V IN , the current I drawn from the input energy source IN ) of different feedback / feedforward signal lines 1735. In some embodiments, the controller 1732 may include a feedforward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B , connected to circuit 1730 as shown in .

[0256] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 1732 can be operated to control the on / off state and on / off timing of switches in a front-end stage 1740 via a first set of one or more signal lines (e.g., circuit connections) 1734, thereby controlling the front-end stage 1740. A second set of one or more controllers 1732 can be operated to control the on / off state and on / off timing of switches in an NRHPZ converter 1755 via a second set of one or more signal lines (e.g., circuit connections) 1734, thereby controlling the NRHPZ converter 1755. A third set of one or more controllers 1732 can be operated to control the on / off state and / or on / off timing of switches in an SC converter 1760 via a third set of one or more signal lines (e.g., circuit connections) 1734, thereby controlling the SC converter 1760.

[0257] In some embodiments, the first set of one or more controllers 1732 can operate the switches in the front-end stage 1740 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 1732 can operate the switches in the NRHPZ converter 1755 and / or the frequency and / or duty cycle at which the third set of one or more controllers 1732 can operate the switches in the SC converter 1760. In some embodiments, the third set of one or more controllers 1732 can operate the switches in the SC converter 1760 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the first set of one or more controllers 1732 can operate the switches in the front-end stage 1740 and / or the frequency and / or duty cycle at which the second set of one or more controllers 1732 can operate the switches in the NRHPZ converter 1755. For example, the duty cycle at which the switches in the front-end stage 1740 and / or the SC converter 1760 operate can depend on the detailed topology and operating mechanism (e.g., slow switching limit versus fast switching limit). In some embodiments, the first set of one or more controllers 1732 can control the switches of the front-end stage 1740 at a duty cycle of approximately 50%. In some embodiments, the third set of one or more controllers 1732 can operate the switches in the SC converter stage 1760 at a duty cycle of approximately 50%.

[0258] In some embodiments, the switches of the front-end stage 1740 can be operated independently of the switches of the NRHPZ converter 1755 and / or the SC converter 1760. In some embodiments, the switches of the SC converter 1760 can be operated independently of the switches of the front-end stage 1740 and / or the NRHPZ converter 1755. In some embodiments, a first set of one or more controllers 1732 can receive a first set of one or more feedback / feedforward signals 1735, a second set of one or more controllers 1732 can receive a second set of feedback / feedforward signals 1735 that can be different from the first set of feedback / feedforward signals 1735, and a third set of one or more controllers 1732 can receive a third set of feedback / feedforward signals 1735 that is different from the first and second sets of feedback / feedforward signals 1735.

[0259] Figure 17C An example circuit 1770 is shown that may include a single NRHPZ converter 1780 and a multiple output switched capacitor converter 1790. The circuit 1770 may be capable of synthesizing multiple different output voltages—with a maximum output voltage up to 1.5*V IN Here Figure 17C The multi-output switched capacitor converter 1790 shown in FIG. Figure 17B The same topology as the multi-output switched capacitor converter 1760 of the embodiment of the present invention. However, unlike the circuit 1730, the circuit 1770 may not have a front end (e.g., a switched capacitor front end). Therefore, the maximum voltage output by the NRHPZ converter 1780 (e.g., a buck converter) may be V IN , and the maximum output voltage of the multi-output switched capacitor converter 1790 can be 1.5*V at V3 IN Therefore, by controlling the switch S 1A 、S 1B 、S 1C 、S 1D 、S 1E 、S 1F 、S 2A 、S 2B 、S 2C 、S 2D 、S 2E and S 2F The on / off state can synthesize 0V and 1.5*V IN In some embodiments, the multi-output switched capacitor converter 1790 can optionally be selectively fed at different voltage rails by introducing additional selector switches (not shown), thereby achieving greater reconfigurability.

[0260] One or more controllers 1775 may control switches (eg, S A1、S A2 、S B1 、S B2 , S3, S4, S5, S 1A 、S 1B 、S 1C 、S 1D 、S 1E 、S 1F 、S 2A 、S 2B 、S 2C 、S 2D 、S 2E 、S 2F ) and optionally additional selector switches to generate the desired output voltages V1, V2, V3. For example, the controller 1775 may alternate between two switching configurations per cycle (for two-phase operation) or three switching configurations per cycle (for three-phase operation) to synthesize the desired output voltages V1, V2, and / or V3, as previously discussed. The controller 1770 may be configured as described for Figure 1B The controller 155 is implemented as described above, but based on a different architecture of the circuit 1730, with different signal lines 1777 for controlling different switches of the circuit 1775, and with different signal lines 1778 for detecting different feedback / feedforward signals (e.g., voltage V1, voltage V2, voltage V3, capacitors (e.g., C1, C2, C3, C f1 、C f2 、C f3 、C f4 、C f5 ) voltage, the current of the inductor L (for example, i L ), the current from voltage V1 to the load, the current from voltage V2 to the load, the current from voltage V3 to the load, the input voltage V IN , the current I drawn from the input energy source IN ) of different feedback / feedforward signal lines 1778. In some embodiments, the controller 1775 may include a feedforward current shaping controller, such as Figure 18A or Figure 18B controller 1805 and can be as Figure 18A or Figure 18B , connected to circuit 1775 as shown.

[0261] In some embodiments, one or more controllers can be used to operate some switches in a circuit, while one or more other controllers can be used to operate other switches in the circuit. For example, a first set of one or more controllers 1775 can be operated to control the on / off state and on / off timing of switches in an NRHPZ converter 1780 via a first set of one or more signal lines (e.g., circuit connections) 1777, thereby controlling the NRHPZ converter 1780. A second set of one or more controllers 1775 can be operated to control the on / off state and on / off timing of switches in an SC converter 1790 via a second set of one or more signal lines (e.g., circuit connections) 1777, thereby controlling the SC converter 1790. In some embodiments, the first set of one or more controllers 1775 can operate the switches in the NRHPZ converter 1780 at a frequency and / or duty cycle that is different from the frequency and / or duty cycle at which the second set of one or more controllers 1775 can operate the switches in the SC converter 1790. For example, the duty cycle at which the switches in the SC converter 1790 operate can depend on the detailed topology and operating mechanism (e.g., slow switching limit vs. fast switching limit). In some embodiments, the second set of one or more controllers 1775 can control the switches of the SC converter 1790 at a duty cycle of approximately 50%. In some embodiments, the switches of the NRHPZ converter 1780 can operate independently of the switches of the SC converter 1790. In some embodiments, a first set of one or more controllers 1775 may receive a first set of one or more feedback / feedforward signals 1778, and a second set of one or more controllers 1775 may receive a second set of feedback / feedforward signals 1778 that may be different from the first set of feedback / feedforward signals 1778.

[0262] Load current feedforward control

[0263] In some implementations, it may be desirable to control one or more NRHPZ converters via a load current feed-forward control mechanism. Figure 18A An example system architecture 1800 for implementing a load current feed-forward control mechanism for one or more NRHPZ converters 1845 is shown. The circuit 1800 may include one or more NRHPZ converters 1845 and one or more NRHPZ controllers 1805. In some embodiments, the NRHPZ controller 1805 may be configured as described for Figure 1BThe controller 155 is implemented as described above, but based on the architecture of the circuit 1800, with a signal line 1820 for controlling the different switches of the NRHPZ converter 1845, and with feedback / feedforward signal lines 1815, 1825, 1830, 1835. For example, the NRHPZ controller 1805 may receive a voltage representing the input voltage V IN One or more signals 1815, representing the output voltage V O The NRHPZ controller 1805 may include one or more signals 1830 representing a load current, one or more signals 1835 representing a load current, and one or more signals representing one or more states of the NRHPZ converter 1845. Signals 1830 may include, for example, state variables of the converter, such as signals representing the inductor current and / or capacitor voltage of the NRHPZ converter 1845. In some embodiments, the NRHPZ controller 1805 may receive one or more reference commands 1810, such as commands from a user or from another device or system (e.g., another device or system with a mobile device, such as within a mobile phone). Reference commands 1810 may include any type of command, including, for example, commands for a desired output voltage (e.g., an output voltage reference) or a desired load current reference. Based on one or more of the feedback / feedforward signals and / or the reference commands, the NRHPZ controller 1805 may send one or more signals on one or more signal lines 1820 to control the NRHPZ converter 1845. For example, the NRHPZ controller 1805 can send pulse width modulation (PWM) signals on signal line 1820 to control one or more switches within the NRHPZ converter 1845 to achieve the desired switching state for a particular phase of the cycle. Based on these signals, the NRHPZ converter 1845 can then output voltage and current to the load 1840 (e.g., one or more power amplifiers).

[0264] The NRHPZ controller 1805 can be used as previously described Figures 1A to 6C and Figures 9 to 17C Any of the controllers discussed herein may be used to control their respective circuits. For example, the NRHPZ controller 1805 may be used to control switches in a magnetic regulation stage, such as previously described. Figures 1A to 6C and Figures 9 to 17C That is, the NRHPZ controller 1805 can be used to control the magnetic stage described (e.g., a 3-level buck converter). Figure 1B The controller 155 of the circuit 150 is used to control Figure 2A The controller 205 of the circuit 200 is used to control Figure 2B The controller 255 of the circuit 250 is used to control Figure 2C The controller 275 of the circuit 275 is used to control Figure 3A The controller 305 of the circuit 300 is used to control Figure 3B The controller 370 of the circuit 350 is used to control Figure 4 The controller 405 of the circuit 400 is used to control Figure 5 The controller 505 of the circuit 500 is used to control Figure 6A The controller 605 of the circuit 600 is used to control Figure 6B The controller 612 of the circuit 640 is used to control Figure 6C The controller 690 of the circuit 670 is used to control Figure 9 The controller 905 of the circuit 900 is used to control Figure 10 The controller 1005 of the circuit 1000 is used to control Figure 11 The controller 1105 of the circuit 1100 is used to control Figure 12 The controller 1205 of the circuit 1200 is used to control Figure 13 The controller 1305 of the circuit 1300 is used to control Figure 14A The controller 1405 of the circuit 1400 is used to control Figure 14B The controller 1455 of the circuit 1450 is used to control Figure 15 The controller 1505 of the circuit 1500 is used to control Figure 16A The controller 1605 of the circuit 1600 is used to control Figure 16B The controller 1655 of the circuit 1650 is used to control Figure 17A The controller 1705 of the circuit 1700 is used to control Figure 17B The controller 1732 of the circuit 1730, or the controller 1732 for controlling Figure 17C Controller 1775 of circuit 1770.

[0265] Those skilled in the art will recognize how to implement any of the previously discussed circuits to Figure 18A 18. For example, the NRHPZ controller 1800 will use signal lines 1820 to control the various switches of the NRHPZ converter (e.g., a 3-level buck converter) in the previously discussed circuits. That is, signal lines 1820 will correspond to one or more of the signal lines described for each of these circuits (e.g., Figure 1B The signal line 157 of the circuit 150, Figure 2A The signal line 207 of the circuit 200, Figure 2B The signal line 257 of the circuit 250, Figure 2C The signal line 282 of the circuit 275, Figure 3A The signal line 307 of the circuit 300, Figure 3BThe signal line 373 of the circuit 350, Figure 4 The signal line 407 of the circuit 400, Figure 5 The signal line 507 of the circuit 500, Figure 6A The signal line 607 of the circuit 600, Figure 6B The signal line 613 of the circuit 640, Figure 6C The signal line 692 of the circuit 670, Figure 9 The signal line 907 of the circuit 900, Figure 10 The signal line 1005 of the circuit 1000, Figure 11 The signal line 1107 of the circuit 1100, Figure 12 The signal line 1207 of the circuit 1200, Figure 13 The signal line 1307 of the circuit 1300, Figure 14A The signal line 1407 of the circuit 1400, Figure 14B The signal line 1466 of the circuit 1450, Figure 15 The signal line 1507 of the circuit 1500, Figure 16A The signal line 1607 of the circuit 1600, Figure 16B The signal line 1657 of the circuit 1650, Figure 17A The signal line 1707 of the circuit 1700, Figure 17B The signal line 1734 of the circuit 1730 or Figure 17C signal line 1777 of circuit 1770).

[0266] The NRHPZ controller 1805 will further receive feedback / feedforward signals for the various NRHPZ converters (e.g., 3-level buck converters) in the previously discussed circuits using feedback / feedforward signals 1815, 1825, 1830, 1835. That is, the input voltage signal 1815, the converter state signal 1825, the output voltage signal 1830, and the load current signal 1835 will correspond to the corresponding one or more feedback / feedforward signals described for each of these circuits (e.g., Figure 1B The feedback / feedforward signal 158 of the circuit 150, Figure 2A The feedback / feedforward signal 208 of the circuit 200, Figure 2B The feedback / feedforward signal 258 of the circuit 250, Figure 2C The feedback / feedforward signal 283 of the circuit 275, Figure 3A The feedback / feedforward signal 308 of the circuit 300, Figure 3B The feedback / feedforward signal 374 of the circuit 350, Figure 4 The feedback / feedforward signal 408 of the circuit 400, Figure 5 The feedback / feedforward signal 508 of the circuit 500, Figure 6AThe feedback / feedforward signal 608 of the circuit 600, Figure 6B The feedback / feedforward signal 614 of the circuit 640, Figure 6C The feedback / feedforward signal 693 of the circuit 670, Figure 9 The feedback / feedforward signal 908 of the circuit 900, Figure 10 The feedback / feedforward signal 1008 of the circuit 1000, Figure 11 The feedback / feedforward signal 1108 of the circuit 1100, Figure 12 The feedback / feedforward signal 1208 of the circuit 1200, Figure 13 The feedback / feedforward signal 1308 of the circuit 1300, Figure 14A The feedback / feedforward signal 1408 of the circuit 1400, Figure 14B The feedback / feedforward signal 1467 of the circuit 1450, Figure 15 The feedback / feedforward signal 1508 of the circuit 1500, Figure 16A The feedback / feedforward signal 1608 of the circuit 1600, Figure 16B The feedback / feedforward signal 1658 of the circuit 1650, Figure 17A The feedback / feedforward signal 1708 of the circuit 1700, Figure 17B The feedback / feedforward signal 1735 of the circuit 1730, Figure 17C 1770 of the circuit 1770). The NRHPZ controller 1805 will further optionally receive the feedback / feedforward signal 1778 as previously described with respect to the previous circuit (see Figure 1B One or more input command signals described by the controller 155) are used as reference commands 1810.

[0267] Figure 18B Circuit 1800 is shown again, but with additional details regarding the operation of NRHPZ controller 1805. Figure 18B As shown in FIG, the NRHPZ controller 1805 may also include a current control subsystem 1870, a feedforward current shaping subsystem 1865, and a feedback control subsystem 1860. The feedback control system may receive one or more signals, such as those previously described with respect to Figure 18A or one or more of the feedback signals discussed with respect to any of the other circuits previously discussed. Figure 18B In the example shown in FIG, the feedback control subsystem 1860 may receive a voltage representing an input voltage V IN One or more signals 1815 and an output voltage V O One or more signals 1830. Figure 18B In the example shown in FIG, the feedback control subsystem 1860 may also receive one or more reference command signals 1810. Based on the signals it receives (e.g., Figure 18Bsignals 1810 , 1815 , and 1830 in the example of FIG, the feedback control subsystem 1860 may provide one or more feedback control signals 1855 to the current control subsystem 1870 .

[0268] The feed-forward current shaping subsystem 1865 may receive one or more signals, such as those previously described with respect to Figure 18A Or one or more of the feedforward signals discussed with respect to any of the other circuits previously discussed. Figure 18B In the example shown in FIG, the feed-forward current shaping subsystem 1865 may receive a voltage representing an input voltage V IN One or more signals 1815, representing the output voltage V O One or more signals 1830 and a signal representing the inductor current i L The load current 1835 may also be provided to the NRHPZ controller 1805 for feed-forward current control. Figure 18B In the example shown in , the feed-forward current shaping subsystem 1865 may also receive one or more reference command signals 1810. Based on the signals it receives (e.g., Figure 18B In the example of signals 1810, 1815, 1830, 1835), the feed-forward current shaping subsystem 1865 can provide one or more feed-forward control signals 1850 to the current control subsystem 1870.

[0269] The current control subsystem 1870 may receive one or more signals, such as those previously described with respect to Figure 18A or one or more of the feedback / feedforward signals discussed with respect to any of the other circuits previously discussed. Figure 18B In the example shown in FIG, the current control subsystem 1870 may receive a current indicating the output voltage V O One or more signals 1830 representing the state of the converter and one or more signals 1825 representing the state of the converter. Figure 18B In the example of , the current control subsystem 1870 may also receive one or more reference command signals 1810. Figure 18B In the example of , the current control subsystem 1870 may also receive one or more feedback control signals 1855 from the feedback control subsystem 1860 and one or more feedforward control signals 1850 from the feedforward current shaping subsystem 1865. Based on the signals it receives (e.g., Figure 18BThe current control subsystem 1870 may output a signal 1820 via one or more signal lines for controlling one or more switches in the one or more NRHPZ converters 1845. For example, the current control subsystem 1870 may output one or more PWM signals via the signal lines to control the on / off state of the switches to a desired switching configuration for each phase of the cycle.

[0270] Although no further details are provided regarding the components within the current control subsystem 1870, the feedforward current shaping subsystem 1865, and the feedback control subsystem 1860, one skilled in the art will recognize that further circuitry will be included within these subsystems (e.g., such as circuitry for Figure 1B A person skilled in the art will understand how to construct a feedback control subsystem that can be based on a circuit representing the output voltage V O One or more signals 1830 representing the input voltage V IN The one or more signals 1815 and the one or more reference commands 1810 provide one or more feedback control signals 1855 to the current control subsystem 1870. A person skilled in the art will further understand how to construct a feed-forward current shaping subsystem 1865, which can be based on a current shaping signal representing the output voltage V O One or more signals 1830 representing the load current, one or more signals 1835 representing the input voltage V IN The one or more signals and one or more reference command signals 1810 provide one or more feedforward command signals 1850 to the current control subsystem 1870. A person skilled in the art will also understand how to construct the current control subsystem 1870, which can be based on the output voltage V O One or more signals 1830, one or more signals 1825 representing the converter stage, one or more reference command signals 1810, one or more feedback control signals 1855 from the feedback control subsystem 1860, and one or more feedforward command signals from the feedforward current shaping subsystem 1865 provide one or more output signals 1820 (e.g., PWM signals) to one or more NRHPZ converters 1845.

[0271] Three-level NRHPZ conversion with two-phase, three-phase and / or N-phase operation

[0272] As previously discussed, the three-level NRHPZ converter described herein can be used with either two-phase control or three-phase control. Three-phase control refers to the ability to control the converter's switching configuration in three different phases per cycle, as opposed to two-phase control where the converter's switching configuration can be controlled in two different phases per cycle.

[0273] The three-level NRHPZ converter discussed previously can be used with three-phase control to generate 0V and the highest voltage V H For example, the output voltage can be selected between two or more available input voltages (e.g., Figure 9 In the example of 0V, V IN 、V H ) alternates between V X The desired output voltage can then be achieved by applying one of the input voltages at a specific duty cycle for one phase of the cycle and filling one or more remaining phases of the cycle with one or more other input voltages. Voltage mode control, current mode control or feed-forward current control (see e.g. Figure 18A 、 Figure 18B and corresponding discussion) can also be used to control the timing of selecting a particular input voltage within a cycle. For example, a voltage or current, such as the input voltage, the current drawn from the energy source, the output voltage, the load current, and / or the voltage or current measured at the component, can be monitored, and the controller can change from one switching configuration to another switching configuration within a cycle based on the monitored values. If the desired output voltage is, for example, V IN , and the monitored output voltage is below V IN , then one or more controllers (see, for example, reference herein to Figures 1A to 6C and Figures 9 to 18B The controller discussed) can operate the switches of the converter so that V X Receive input voltage V H , to increase the output voltage of the converter. Once the output voltage is higher than V IN , the converter can operate the switch so that V X Receive V IN or 0V input voltage to reduce the output voltage closer to V IN .

[0274] Consider Figure 9 The circuit 900 is used as an example, for 0V up to close to V IN The output voltage between 0V and V IN The voltage between V XTo synthesize the desired output voltage. This is an example of two-phase operation. To synthesize a voltage higher than V IN The output voltage, voltage V X Can be in V IN and V H This is another example of two-phase operation. In some embodiments, three-phase operation can be used to synthesize a voltage close to V IN output voltage.

[0275] For example, in Figure 9 In the circuit 900, in the "low range" (eg, the output voltage V OUT Less than V IN ) or "high range" (e.g., output voltage V OUT Greater than V IN ), the control of the magnetic regulation stage over the switching cycle can be divided into two phases. The first phase (e.g., phase 1) can have a duty cycle D, and the second phase (e.g., phase 2) can have a duty cycle of 1-D. To achieve periodic steady-state operation, one phase can apply a zero or positive voltage to the inductor (so that di L / dt>=0), and the other phase can apply zero or negative voltage on the inductor (so that di L / dt<=0), where the steady-state voltage is such that the average voltage across the inductor during the switching cycle in periodic steady-state operation can be zero ( <d iL There are many ways to determine the value of the duty cycle in the manner described above, for example by voltage mode control or current mode control, or load feedforward current control, including for example average, peak and / or valley current mode control. Figure 9 For the circuit 900 shown in FIG, the switching possibilities listed in Table 5 below may be typical. In Table 5, the "Mode" column is for Figure 9 The circuit 900 lists various switching modes as examples. The "Mode Used" column lists what output voltage values ​​can be synthesized by using this mode. The "Phase 1: di / dt>=0" column lists the voltage V during phase 1 of the switching cycle. X The "Phase 2: di / dt <= 0" column lists the voltage V during phase 2 of the switching cycle. X The value of .

[0276] Table 5

[0277] model Mode Usage Phase 1: di / dt >=0 Phase 2: di / dt <= 0 1 <![CDATA[Low V OUT > <![CDATA[V X =V IN ]]> <![CDATA[V X =0]]> 2 <![CDATA[Any V OUT > <![CDATA[V X =V H ]]> <![CDATA[V X =0]]> 3 <![CDATA[High V OUT > <![CDATA[V X =V H ]]> <![CDATA[V X =V IN ]]> 4 <![CDATA[Bypass V OUT = V IN > <![CDATA[V X =V IN ]]> <![CDATA[V X =V IN ]]>

[0278] The different two-phase switching modes provided in Table 5 can provide different capabilities in terms of the periodic steady-state voltage conversion ratio of the magnetic regulation stage. Mode 1 (“Low”) can enable a voltage equal to or less than the input voltage VIN Mode 3 (“High”) can enable a voltage equal to or greater than the input voltage V IN , until the voltage V H Mode 2 ("Any") can be obtained between 0V and V H Any output voltage range between V OUT , but this mode may impose a relatively high degree of stress and loss on components for a given conversion ratio compared to Mode 1 or Mode 3. Therefore, if this mode is used, it may be inefficient and may require larger components than the other modes. Mode 4 ("Bypass") can reduce the input voltage V IN Connect to the output voltage V OUT , thus providing a conversion ratio of 1, but in practice slightly less than 1 due to component voltage drops. Therefore, some degree of control complexity may be desirable to achieve a voltage close to the input voltage V without high stress on the components. IN The output voltage V OUT .

[0279] In the converters discussed previously, for at least some desired ranges of voltage conversion ratios, the operation of the magnetic regulation stage can be extended beyond the two-phase operating mode. That is, three or more sets of switch states can be utilized over the switching (i.e., operating cycle) cycle of the magnetic regulation stage. Such an operating mode using 3 or more sets of switch states can be referred to as "three-phase" control and can be implemented in various ways, including using voltage mode control, current mode control, or load current feedforward control. A converter using three-phase control can provide voltage conversion for conversion ratios <1, =1, and >1, so that it may be more efficient than a converter using a two-phase (i.e., 2 switch states per cycle) approach, while still allowing a wide operating range and low component stress. It may also be desirable to provide such a three-phase converter efficiently and compactly with a relatively simple circuit that retains other capabilities that may be desired, such as current mode control, high regulation bandwidth, and simple compensation with smooth mode transitions. It may also be valuable to achieve a smooth transition between conventional two-phase control and three-phase operating modes. This can be achieved using three-phase control techniques, but by using three phases of three-phase control, which are achieved by one phase having V X =V IN , the second phase has V X =V H , and the third phase has V X = 0 (not necessarily in this switching order). The order and control of the switching can be arranged in any number of ways.

[0280] It should be understood that while examples are described herein with reference to two-phase or three-phase operating modes, such references are intended solely to facilitate clarity in the description of the broad concepts sought to be protected and are not intended to be, and should not be construed as, limiting. For example, after reading the description provided herein, it will be apparent to one of ordinary skill in the art that the concepts, systems, system architectures, circuits, methods, and techniques described herein can be extended to even more than three phases per cycle. In fact, any integer number of phases N can be used per cycle by turning on a selected group of switches in each of the N phases per cycle. This can be referred to as N-phase control.

[0281] In the embodiments disclosed herein, the switch group to be switched on or off in a phase of a cycle may include one or more switches. Although some examples provided herein may describe a specific switch group for a phase or mode, and some may not, after reading the examples and descriptions, one of ordinary skill in the art will understand how many and which switches may be included in a phase of a cycle.

[0282] Decisions regarding how many phases to include in a cycle, which switch states of switches in the circuit to include in each phase of the cycle, and / or when to switch between phases / switch states in a cycle may be made by one or more controllers (see, e.g., Figure 1B Controller 155, Figure 2A Controller 205, Figure 2C Controller 280, Figure 3A Controller 305, Figure 3B Controller 370, Figure 4 Controller 405, Figure 5 Controller 505, Figure 6A Controller 605, Figure 6B Controller 612, Figure 6C Controller 690, Figure 9 Controller 905, Figure 10 Controller 1005, Figure 11 Controller 1105, Figure 12 Controller 1205, Figure 13 Controller 1305, Figure 14A Controller 1405, Figure 14B Controller 1455, Figure 15 Controller 1505, Figure 16A Controller 1605, Figure 16B Controller 1655, Figure 17A Controller 1705, Figure 17B Controller 1732, Figure 17C Controller 1775, Figure 18A and Figure 18B Controller, Figure 19 In some embodiments, these decisions can be based at least in part on one or more feedback / feedforward signals (see, e.g., Figure 1B Feedback / feedforward signal 158, Figure 2A Feedback / feedforward signal 208, Figure 2B Feedback / feedforward signal 258, Figure 2C Feedback / feedforward signal 283, Figure 3A Feedback / feedforward signal 308, Figure 3B Feedback / feedforward signal 374, Figure 4 Feedback / feedforward signal 408, Figure 5 Feedback / feedforward signal 508, Figure 6A Feedback / feedforward signal 608, Figure 6B Feedback / feedforward signal 614, Figure 6C Feedback / feedforward signal 693, Figure 9 Feedback / feedforward signal 908, Figure 10 Feedback / feedforward signal 1008, Figure 11 Feedback / feedforward signal 1108, Figure 12 Feedback / feedforward signal 1208, Figure 13 Feedback / feedforward signal 1308, Figure 14A Feedback / feedforward signal 1408, Figure 14B Feedback / feedforward signal 1467, Figure 15 Feedback / feedforward signal 1508, Figure 16A Feedback / feedforward signal 1608, Figure 16B Feedback / feedforward signal 1658, Figure 17A Feedback / feedforward signal 1708, Figure 17B Feedback / feedforward signal 1735, Figure 17C Feedback / feedforward signal 1778, Figure 18A and Figure 18B Feedback / feedforward signal, Figure 19 The one or more controllers may control the current state of the circuit by means of one or more switch control signal lines (see, for example, Figure 1B Signal line 157, Figure 2A Signal line 207, Figure 2B Signal line 257, Figure 2C Signal line 282, Figure 3A Signal line 307, Figure 3B Signal line 373, Figure 4 Signal line 407, Figure 5 Signal line 507, Figure 6A Signal line 607, Figure 6B Signal line 613, Figure 6C Signal line 692, Figure 9 Signal line 907, Figure 10 Signal line 1007, Figure 11 Signal line 1107, Figure 12 Signal line 1207, Figure 13 Signal line 1307, Figure 14A Signal line 1407, Figure 14B Signal line 1466, Figure 15 Signal line 1507, Figure 16A Signal line 1607, Figure 16B Signal line 1657, Figure 17A Signal line 1707, Figure 17B Signal line 1734, Figure 17C Signal line 1777, Figure 18A and Figure 18B signal lines, Figure 19 The controllers may control the switches in each phase of the cycle by pulsing the signals on or off (e.g., at a certain duty cycle) on the signal lines of each switch to be controlled, such as by pulse width modulation (PWM) control of the signals on the signal lines, to place the switches in their correct states for the switch configurations in a particular phase of the cycle.

[0283] In some embodiments, these decisions can be made before a switching cycle (i.e., an operating cycle) begins. For example, one or more controllers can determine how many phases to include in a cycle and what on / off states each of the switches in the circuit should have for each phase of the cycle based on configuration information stored in the one or more controllers, and control the switches accordingly. In some embodiments, the one or more controllers can take into account feedback / feedforward information about the current state of the circuit from any of the previously discussed feedback / feedforward signals when making these decisions.

[0284] In some embodiments, these decisions can be made on the fly. That is, within a cycle, one or more controllers can take into account information about the current state of the circuit from any of the previously discussed feedback and / or feedforward signals and, within that cycle, select the configuration of switches for the next phase accordingly to achieve the desired output. For example, if the desired output voltage is V IN and receives an indication much smaller than V IN If a signal of the current output voltage is provided, one or more controllers can control the switches to output a higher voltage (e.g., V X V H) to increase the output voltage. In some embodiments, one or more controllers can control the NRHPZ converter to use three switching configurations (three-phase operation) in one cycle and two switching configurations (two-phase operation) in the next cycle, or vice versa, and can smoothly switch between three-phase operation and two-phase operation.

[0285] In some embodiments, different types of feedback / feedforward information may be used in different operating cycles of the converter. For example, voltage-mode control may be used to determine which switching configurations to use in one operating cycle, while current-mode control (including, for example, load current feedforward control) may be used to determine which switching configurations to use in another operating cycle.

[0286] A person of ordinary skill in the art will recognize upon reading this disclosure that Figures 1A to 18B Certain circuits within the described circuits may be used together to create additional circuits with additional benefits, depending on the particular application. For example, one skilled in the art will recognize that certain front-end switched capacitor converters and / or magnetic front ends may be used with (e.g., in parallel or cascade) one or more magnetic converters (e.g., a 3-level buck converter), depending on the application, and may be used with one or more multi-output switched capacitor converters. One skilled in the art will recognize that any combination of the front-end circuits and / or output converter circuits discussed herein may be used in combination with an NRHPZ converter, and all such combinations should be considered within the spirit and scope of the present disclosure provided herein.

[0287] Figure 19 An example process 1900 is shown that can be used to implement a switch configuration in two-phase operation of a converter, as previously discussed. In some embodiments, the process 1900 can be, for example, a process previously described with respect to Figures 1A to 18B In some embodiments, process 1900 may be implemented by a processor in one or more of the controllers discussed above. Figures 1A to 18B In some embodiments, the process 1900 may be implemented in an application specific integrated circuit (ASIC) in one or more of the controllers discussed above. Figures 1A to 18B In some embodiments, the process 1900 may be implemented in a digital logic component in one or more of the controllers discussed above. Figures 1A to 18B is implemented in an analog component in one or more of the controllers in question.

[0288] At 1910, one or more signals may be received. For example, a controller (e.g., Figures 1A to 18BOne or more of the controllers described herein may receive one or more feedback and / or feedforward signals (e.g., regarding Figures 1A to 18B In some embodiments, the one or more signals may be one or more input commands or reference command signals (e.g., as previously described with respect to Figures 1A to 18B one or more of the input command signals or reference command signals described herein).

[0289] In 1920, for the first phase of the operating cycle, the circuit (e.g., Figures 1A to 18B One or more switches in one or more of the described circuits may be set to an on or off state for a particular first switch configuration. For example, based on the feedback / feedforward signal, input command signal, and / or reference command signal received in 1910, the controller (e.g., regarding Figures 1A to 18B One of the controllers described herein) can select the desired switch configuration and Figures 1A to 18B outputting a signal on one or more of the signal lines in question) to set the switches of the circuit to that switch configuration.

[0290] At 1930, for a second phase of the operating cycle, one or more switches of the circuit may be set to an on or off state for a particular second switching configuration. The second switching configuration may be determined, for example, based on one or more additional feedback signals, feedforward signals, reference command signals, and / or input command signals received since setting the first switching configuration, or may be based on previously received signals.

[0291] Figure 20 An example process 2000 is shown that can be used to implement a switch configuration in three-phase operation of a converter, as previously discussed. In some embodiments, the process 2000 can be, for example, a process previously described with respect to Figures 1A to 6C and Figures 9 to 18B In some embodiments, the process 2000 may be implemented by a processor in one or more of the controllers discussed above. Figures 1A to 6C and Figures 9 to 18B In some embodiments, the process 2000 may be implemented in an application specific integrated circuit (ASIC) in one or more of the controllers discussed above. Figures 1A to 6C and Figures 9 to 18B In some embodiments, the process 2000 may be implemented in a digital logic component in one or more of the controllers discussed above. Figures 1A to 6C and Figures 9 to 18B is implemented in an analog component in one or more of the controllers in question.

[0292] In 2010, one or more signals may be received. For example, a controller (e.g., Figures 1A to 6C and Figures 9 to 18B One or more of the controllers described herein may receive one or more signals (e.g., regarding Figures 1A to 6C and Figures 9 to 18B In some embodiments, the one or more signals may include one or more input command or reference command signals (e.g., as previously described with respect to Figures 1A to 6C and Figures 9 to 18B one or more of the input command signals or reference command signals described herein).

[0293] In 2020, for the first phase of the operating cycle, one or more switches of the circuit (e.g., Figures 1A to 6C and Figures 9 to 18B One or more of the circuits described herein) can be set to an on or off state for a particular first switch configuration. For example, based on the feedback / feedforward signal, input command signal, and / or reference command signal received in 2010, the controller (e.g., regarding Figures 1A to 6C and Figures 9 to 18B One of the controllers described herein) can select the desired switch configuration and Figures 1A to 6C and Figures 9 to 18B outputting a signal on one or more of the signal lines in question) to set the switches of the circuit to that switch configuration.

[0294] At 2030, for a second phase of the operating cycle, one or more switches of the circuit may be set to an on or off state for a particular second switching configuration. The second switching configuration may be determined, for example, based on one or more additional feedforward and / or feedback signals, reference command signals, and / or input command signals received since setting the first switching configuration, or may be based on previously received signals.

[0295] At 2040, for a third phase of the operating cycle, one or more switches of the circuit may be set to an on or off state for a particular third switching configuration. The third switching configuration may be determined, for example, based on one or more additional feedforward and / or feedback signals, reference command signals, and / or input command signals received since setting the first switching configuration, or may be based on previously received signals.

[0296] Although about Figure 19 and Figure 20A plurality of switch configurations are described, but these switch configurations can be different or the same as each other. For example, for process 2000, in some embodiments, the first switch configuration and the second switch configuration can be the same, the first switch configuration and the third switch configuration can be the same, or the second switch configuration and the third switch configuration can be the same.

[0297] Figure 21 An example process 2100 is shown that can be used to implement a switch configuration over multiple operating cycles of a converter, as previously discussed. In some embodiments, the process 2100 can be, for example, a process previously described with respect to Figures 1A to 6C and Figures 9 to 18B In some embodiments, the process 2100 may be implemented by a processor in one or more of the controllers discussed above. Figures 1A to 6C and Figures 9 to 18B In some embodiments, the process 2100 may be implemented in an application specific integrated circuit (ASIC) in one or more of the controllers discussed above. Figures 1A to 6C and Figures 9 to 18B In some embodiments, the process 2100 may be implemented in a digital logic component in one or more of the controllers discussed above. Figures 1A to 6C and Figures 9 to 18B is implemented in an analog component in one or more of the controllers in question.

[0298] At 2110, one or more signals may be received. For example, a controller (e.g., Figures 1A to 6C and Figures 9 to 18B One or more of the controllers described herein may receive one or more signals (e.g., regarding Figures 1A to 6C and Figures 9 to 18B In some embodiments, the one or more signals may include one or more input command or reference command signals (e.g., as previously described with respect to Figures 1A to 6C and Figures 9 to 18B one or more of the input command signals or reference command signals described herein).

[0299] In 2020, for multiple phases of the operating cycle (e.g., two for two-phase control, three for three-phase control), one or more switches of the circuit (e.g., about Figures 1A to 6C and Figures 9 to 18B One or more of the circuits described herein) can be set to an on or off state for a particular first switch configuration. For example, based on the feedback and / or feedforward signals, input command signals, and / or reference command signals received in 2010, a controller (e.g., regarding Figures 1A to 6C and Figures 9 to 18B One of the controllers described herein) can select a desired switch configuration for at least one of the phases of an operating cycle and provide a desired switching configuration on a signal line (e.g., with respect to Figures 1A to 6C and Figures 9 to 18B In some embodiments, the switching configuration for all phases of the operating cycle can be determined based on the signal received in 2110. In some embodiments, a first switching configuration for a first phase of the operating cycle can be determined based on the signal received in 2110, and additional switching configurations for additional phases of the operating cycle can be determined based on additional feedback and / or feedforward signals, input command signals, and / or reference command signals received during the operating cycle.

[0300] In 2030, for a plurality of phases (e.g., two for two-phase control, three for three-phase control) of a second operating cycle, one or more switches of the circuit (e.g., Figures 1A to 6C and Figures 9 to 18B One or more of the circuits described herein) can be set to an on or off state for a particular first switch configuration. For example, based on a feedback / feedforward signal, an input command signal, and / or a reference command signal (e.g., as received in 2010 or as received during a previous operating cycle), a controller (e.g., regarding Figures 1A to 6C and Figures 9 to 18B One of the controllers described herein) can select a desired switch configuration for at least one of the phases of the second operating cycle and provide a desired switching configuration on a signal line (e.g., with respect to Figures 1A to 6C and Figures 9 to 18B In some embodiments, the circuit may output a signal on one or more of the signal lines discussed above to set the switches of the circuit to the switching configuration for one or more phases of the operating cycle. In some embodiments, the switching configuration for all phases of the operating cycle can be determined based on the received signal. In some embodiments, a first switching configuration for a first phase of the operating cycle can be determined based on the received signal, and additional switching configurations for additional phases of the operating cycle can be determined based on additional feedforward and / or feedback signals, input command signals, and / or reference command signals received during a second operating cycle.

[0301] In some embodiments, operation cycle 1 of process 2100 can be controlled using two-phase control (see, e.g., Figure 19 1900), and the operation cycle 2 of the process 2100 can be controlled with three-phase control (see, for example Figure 20 In some embodiments, operation cycle 1 of process 2100 may be controlled using three-phase control (see, e.g., Figure 202000), and the operation cycle 2 of the process 2100 can be controlled with two-phase control (see, for example, Figure 19 In some embodiments, operation cycle 1 of process 2100 can be controlled using two-phase control (see, e.g., Figure 19 1900), and the operation cycle 2 of the process 2100 can also be controlled with two-phase control (see, for example Figure 19 In some embodiments, operation cycle 1 of process 2100 may be controlled using three-phase control (see, e.g., Figure 20 2000), and the operation cycle 2 of the process 2100 can also be controlled by three-phase control (see, for example Figure 20 Process 2100 may be directed to, for example, a circuit as previously discussed (e.g., regarding Figures 1A to 6C and Figures 9 to 18B Repeats for each cycle of the converter in any of the circuits described).

[0302] Various embodiments of the concepts, systems, system architectures, circuits, methods, and techniques to be protected are described herein with reference to the accompanying drawings. Without departing from the scope of the concepts, systems, system architectures, circuits, methods, and techniques described herein, alternative embodiments may be designed. Note that in the foregoing description and accompanying drawings, various connections and positional relationships (e.g., above, below, adjacent, etc.) between elements may be described. Unless otherwise indicated, these connections and / or positional relationships may be direct or indirect, and the described concepts, systems, system architectures, circuits, methods, and techniques are not intended to be limited to this aspect. Therefore, the coupling of a component or subsystem may refer to direct or indirect coupling, and the positional relationship between a component or subsystem may be a direct or indirect positional relationship.

[0303] Figures 1A to 18B Circuits are shown with certain components directly connected to each other. One of ordinary skill in the art will understand that each of these components has terminals through which they can be connected to other components by wires, electrical traces, or other conductive lines, as shown in the schematics. Although Figures 1A to 18B Some components may be shown as being directly connected to each other, but the disclosure is not so limited. For example, one or more components may be connected Figures 1A to 18B Schematic diagrams are shown as directly connected between components. Both direct and indirect connections are intended to be encompassed by the present disclosure herein. When a direct connection is indicated herein and in the claims, the word "directly" will be used to indicate the connection between components. Thus, the term "connect" (or any variations thereof) may include both "indirect connections" and "direct connections."

[0304] As used herein, the terms "comprise," "comprising," "include," "including," "has," "having," "contain," "containing," or any other variations thereof, are intended to cover a non-exclusive inclusion. For example, a system, system architecture, subsystem, component, circuit, process, method, article, or apparatus that comprises a list of elements or steps is not necessarily limited to only those elements or steps but may include other elements or steps not expressly listed or inherent to such systems, system architecture, subsystem, component, circuit, process, method, article, or apparatus.

[0305] Furthermore, if the term "exemplary" is used herein, it means "serving as an example, instance, or illustration." Any embodiment or example described herein as "exemplary" is not necessarily to be construed as preferred or advantageous over other embodiments or designs. The term "one or more" is understood to include any integer greater than or equal to one, i.e., one, two, three, four, etc. The term "plurality" is understood to include any integer greater than or equal to two, i.e., two, three, four, five, etc.

[0306] References in the specification to "one embodiment," "an embodiment," "an example embodiment," etc., indicate that the embodiment may include a particular feature, structure, or characteristic, but each embodiment may include the particular feature, structure, or characteristic. Furthermore, these phrases are not necessarily referring to the same embodiment. Furthermore, when a particular feature, structure, or characteristic is described in conjunction with an embodiment, it is understood that it is within the knowledge of those skilled in the art to incorporate such feature, structure, or characteristic in conjunction with other embodiments, regardless of whether or not explicitly described in that manner.

[0307] The use of ordinal terms such as "first," "second," and "third" in the claims to modify claim elements does not in itself imply any priority, precedence, or order of one claim element relative to another claim element or the temporal order of the acts of performing the method, but is merely used as a marker to distinguish one claim element having a certain name from another element having the same name (but using ordinal terms) to distinguish the claim elements.

[0308] The terms "approximately," "substantially," or "about" may be used to mean in some embodiments + / - 30% of a target value, in some embodiments within + / - 20% of a target value, in some embodiments within + / - 10% of a target value, in some embodiments within + / - 5% of a target value, and in some embodiments within + / - 2% of a target value. The foregoing may include a target value. The terms "approximately equal to," "substantially equal to," or "approximately equal to" may be used to mean that in some embodiments, values ​​are within + / - 30% of each other, in some embodiments, values ​​are within + / - 20% of each other, in some embodiments, values ​​are within + / - 10% of each other, in some embodiments, values ​​are within + / - 5% of each other, and in some embodiments, values ​​are within + / - 2% of each other. For example, a first voltage value that is "approximately," "substantially," or approximately equal to a second voltage value can be within + / - 30% of the second voltage value in some embodiments, within + / - 20% of the second voltage value in some embodiments, within + / - 10% of the second voltage value in some embodiments, within + / - 5% of the second voltage value in some embodiments, or within + / - 2% of the second voltage value in some embodiments. The foregoing may be an exact match of values.

[0309] It should be understood that the disclosed subject matter is not limited in its application to the details of construction and arrangement of components set forth in the foregoing description or illustrated in the drawings. The disclosed subject matter is capable of other embodiments and of being practiced and carried out in various ways.

[0310] Furthermore, it should be understood that the phraseology and terminology employed herein are for descriptive purposes only and should not be construed as limiting. Therefore, one skilled in the art will appreciate that the concepts upon which this disclosure is based can readily be used as a basis for designing other structures, systems, system architectures, circuits, methods, and techniques for carrying out the various purposes of the disclosed subject matter. Therefore, the claims should be deemed to include equivalent constructions to the extent such constructions do not depart from the spirit and scope of the disclosed subject matter.

[0311] While the disclosed subject matter has been described and illustrated in the foregoing example embodiments, it should be understood that this disclosure is by way of example only and that many changes may be made in details of its implementation without departing from the spirit and scope of the disclosed subject matter.

Claims

1. A power converter having a pair of input terminals configured to be connected to opposite terminals of a voltage source and having an output terminal configured to be coupled to a load, the power converter comprising: Magnetic grades, including: a first plurality of switches; and Inductors; an output stage coupled to the magnetic stage, the output stage comprising: a second plurality of switches; and at least one capacitor; and One or more controllers configured to control the first plurality of switches to selectively couple the first end of the inductor to a first input terminal of the pair of input terminals, a second input terminal of the pair of input terminals, and a voltage greater than a voltage at the input terminals.

2. The power converter according to claim 1, wherein: The at least one capacitor includes a first capacitor and a second capacitor, and the output stage is configured to: outputting a first voltage at a first terminal coupled to the first capacitor, and A second voltage is output at a second terminal coupled to the second capacitor.

3. The power converter according to claim 1, wherein: The at least one capacitor includes a first capacitor and a second capacitor, and wherein the one or more controllers are further configured to control the second plurality of switches to couple the second end of the inductor to the first capacitor or the second capacitor. 4 . The power converter of claim 1 , further comprising a front-end stage configured to synthesize the voltage greater than the voltage at the input terminal.

5. The power converter according to claim 1, wherein The magnetic stage is configured to provide an output voltage between zero volts and twice the voltage at the input terminal while having no right half-plane zero in a control-to-output transfer function of the magnetic stage.

6. The power converter according to claim 1, wherein The magnetic stage is a first magnetic stage, and the inductor is a first inductor, the power converter further comprising a second magnetic stage comprising: a third plurality of switches; and The second inductor.

7. The power converter according to claim 6, wherein: The one or more controllers are further configured to control the third plurality of switches to selectively couple the first end of the second inductor to the first input terminal of the pair of input terminals, the second input terminal of the pair of input terminals, and the voltage greater than the voltage at the input terminals.

8. The power converter according to claim 7, wherein: The output stage is coupled to the first magnetic stage and the second magnetic stage.

9. The power converter according to claim 8, wherein: The first magnetic stage is configured to output a first voltage, the second magnetic stage is configured to output a second voltage, and the output stage is configured to synthesize at least a third voltage different from the first voltage or the second voltage.

10. The power converter according to claim 9, wherein: The first magnetic stage and the second magnetic stage are connected in parallel with their inputs.

11. The power converter according to claim 9, wherein: The first magnetic stage and the second magnetic stage are connected in cascade. 12 . The power converter of claim 6 , further comprising a front-end stage configured to provide the voltage that is greater than the voltage at the input terminal.

13. The power converter according to claim 9, wherein: The third voltage is the sum of the first voltage and the second voltage.

14. The power converter according to claim 9, wherein: The third voltage is twice the second voltage minus the first voltage.

15. The power converter according to claim 1, wherein The output stage is configured to synthesize at least three different output voltages.

16. The power converter according to claim 5, wherein The output stage is configured to synthesize one or more output voltages ratiometrically related to the output voltage of the magnetic stage.

17. The power converter according to claim 1, wherein The magnetic stage is further configured to: selectively coupling the first end of the inductor to the first input terminal of the pair of input terminals through operation of a first switch; selectively coupling the first end of the inductor to the second input terminal of the pair of input terminals through operation of a second switch; as well as The first end of the inductor is selectively coupled to the voltage greater than the voltage at the input terminal by operation of a third switch.

18. The power converter according to claim 17, wherein: The one or more controllers are configured to control the first switch, the second switch, and the third switch in the magnetic stage to generate a desired voltage output from the magnetic stage.

19. The power converter according to claim 18, wherein: The one or more controllers are further configured to receive one or more signals corresponding to a load current and provide feed-forward control to generate the desired voltage based on the received one or more signals.

20. The power converter according to claim 18, wherein The one or more controllers are configured to control the magnetic stages to synthesize the desired voltage to be lower than the voltage at the input terminal by: operating the first switch to couple the first input terminal of the pair of input terminals to the first end of the inductor during one phase of a switching cycle of the magnetic stage; as well as During another phase of the switching cycle of the magnetic stage, the second switch is operated to couple the second input terminal of the pair of input terminals to the first end of the inductor.

21. The power converter according to claim 18, wherein The one or more controllers are configured to control the magnetic stages to synthesize the desired voltage to be higher than the voltage at the input terminal by: operating the first switch to couple the first input terminal of the pair of input terminals to the first end of the inductor during one phase of a switching cycle of the magnetic stage; as well as During another phase of the switching cycle of the magnetic stage, the third switch is operated to couple the voltage greater than the voltage at the input terminal to the first end of the inductor.

22. The power converter according to claim 18, wherein The one or more controllers are configured to control the magnetic stages to synthesize the desired voltage by: operating the second switch to couple the second input terminal of the pair of input terminals to the first end of the inductor during one phase of a switching cycle of the magnetic stage; as well as During another phase of the switching cycle of the magnetic stage, the third switch is operated to couple the voltage greater than the voltage at the input terminal to the first end of the inductor.

23. The power converter according to claim 18, wherein The one or more controllers are configured to control the magnetic stages to synthesize the desired voltage by: operating the first switch to couple the first input terminal of the pair of input terminals to the first end of the inductor during a first phase of a switching cycle of the magnetic stage; operating the third switch to couple the voltage greater than the voltage at the input terminal to the first end of the inductor during a second phase of the switching cycle of the magnetic stage; as well as During a third phase of the switching cycle of the magnetic stage, the second switch is operated to couple the second input terminal of the pair of input terminals to the first end of the inductor.

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