Information transmission method, communication device and storage medium

Abstract

The application provides an information transmission method, a communication device and a storage medium. The method comprises the following steps: determining a first number of extremely sparse pilots, and then transmitting a data packet and the first number of extremely sparse pilots to a second communication node, wherein the first number is greater than or equal to 1, the data packet contains at least a modulation symbol, the modulation symbol is obtained by modulating M1+1 bit information in the data packet according to a first constellation model, or M2+2 bit information in the data packet according to a second constellation model, or M3+3 bit information in the data packet according to a third constellation model, M1 is an integer greater than or equal to 1, M2 is an integer greater than or equal to 1, and M3 is an integer greater than or equal to 0. Therefore, the embodiment of the application can support a large number of first communication nodes to realize high-spectrum-efficiency information transmission.

Description

Technical Field

[0001] The embodiments of the present application relate to, but are not limited to, the field of communication technology, and in particular to an information transmission method, a communication device, and a storage medium. Background Art

[0002] In scenarios where a wireless communication system is connected to a large number of terminals, the wireless communication system needs to transmit information to these terminals. Furthermore, if the spectrum efficiency of information transmission for each terminal is required to be moderate, it is also necessary to increase the order of the modulation scheme to improve the spectrum efficiency.

[0003] In related technologies, the commonly used high-order modulation method is Quadrature Amplitude Modulation (QAM), such as 16QAM, 32QAM, 64QAM, and 256QAM. However, these high-order modulation methods require relatively accurate channel estimation to ensure performance. If the channel estimation error is large, the constellation diagram will be distorted during demodulation, which will lead to a decrease in demodulation performance, making it difficult to achieve high-spectrum-efficiency information transmission. Moreover, in a scenario where a wireless communication system is connected to a large number of terminals, a large number of terminals transmit information to the system, which will increase the pilot overhead at the terminal. If the pilot overhead is too large, it will be difficult to ensure the accuracy of the channel estimation. Therefore, it will also limit the demodulation performance of the base station or access point, and it will also be difficult to achieve high-spectrum-efficiency information transmission. Therefore, how to support massive terminals to achieve high-spectrum-efficiency information transmission is a problem that needs to be solved urgently. Summary of the Invention

[0004] The embodiments of the present application provide an information transmission method, a communication device, and a storage medium, which can support a large number of first communication nodes to achieve high-spectrum-efficiency information transmission.

[0005] In a first aspect, an embodiment of the present application provides an information transmission method, applied to a first communication node, the information transmission method comprising:

[0006] determining a first number of very sparse pilots;

[0007] transmitting a data packet together with the first number of the very sparse pilots to a second communication node;

[0008] Wherein, the first number is greater than or equal to 1, and the data packet contains at least a modulation symbol;

[0009] The modulation symbol is obtained by modulating M1+1 bits of information in the data packet according to a first constellation model, wherein the first constellation model includes 2*N1 constellation points, M1 is an integer greater than or equal to 1, and N1 and M1 satisfy the formula N1=2 M1 ;

[0010] The complex forms corresponding to the 2*N1 constellation points in the first constellation diagram model include the following:

[0011] a1e jθ ,a2e jθ ,…,a N1 e jθ ,

[0012] a1e j(θ+π) ,a2e j(θ+π) ,…,a N1 e j(θ+π) ;

[0013] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N1 Are all positive numbers and satisfy: 0 <a1<a2<...<a N1 ;

[0014] or,

[0015] The modulation symbol is obtained by modulating M2+2 bits of information in the data packet according to a second constellation model, wherein the second constellation model includes 4*N2 constellation points, M2 is an integer greater than or equal to 1, and N2 and M2 satisfy the formula N2=2 M2 ;

[0016] The complex forms corresponding to the 4*N2 constellation points in the second constellation diagram model include the following:

[0017] a1e jθ ,a2e jθ ,…,a N2 e jθ ,

[0018] b1e j(θ+π / 2) ,b2e j(θ+π / 2) ,…,b N2 e j(θ+π / 2) ,

[0019] a1e j(θ+π) ,a2e j(θ+π) ,…,a N2 e j(θ+π) ,

[0020] b1e j(θ+3π / 2) ,b2e j(θ+3π / 2) ,…,b N2 e j(θ+3π / 2) ;

[0021] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N2 and b1,b2,…,b N2 Are all positive numbers and satisfy: 0 <a1<a2<…<a N2 , 0 <b1<b2<…<b N2 ;

[0022] or,

[0023] The modulation symbol is obtained by modulating M3+3 bits of information in the data packet according to a third constellation model, wherein the third constellation model includes 8*N3 constellation points, M3 is an integer greater than or equal to 0, and N3 and M3 satisfy the formula N3=2 M3 ;

[0024] The complex forms corresponding to the 8*N3 constellation points in the third constellation diagram model include the following:

[0025] a1e jθ ,a2e jθ ,…,a N3 e jθ ,

[0026]

[0027]

[0028]

[0029] a1e j(θ+π) ,a2e j(θ+π) ,…,a N3 e j(θ+π) ,

[0030]

[0031]

[0032]

[0033] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N3 and b1,b2,…,b N3 Are all positive numbers and satisfy: 0 <a1<a2<…<a N3 , 0 <b1<b2<…<b N3 .

[0034] In a second aspect, an embodiment of the present application provides an information transmission method, applied to a second communication node, the information transmission method comprising:

[0035] receiving a data packet and a first number of extremely sparse pilots sent by a first communication node;

[0036] Wherein, the first number is greater than or equal to 1, and the data packet contains at least a modulation symbol;

[0037] The modulation symbol is obtained by modulating M1+1 bits of information in the data packet according to a first constellation model, wherein the first constellation model includes 2*N1 constellation points, M1 is an integer greater than or equal to 1, and N1 and M1 satisfy the formula N1=2 M1 ;

[0038] The complex forms corresponding to the 2*N1 constellation points in the first constellation diagram model include the following:

[0039] a1e jθ ,a2e jθ ,…,a N1 e jθ ,

[0040] a1e j(θ+π) ,a2e j(θ+π) ,…,a N1 e j(θ+π) ;

[0041] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N1 Are all positive numbers and satisfy: 0 <a1<a2<…<a N1 ;

[0042] or,

[0043] The modulation symbol is obtained by modulating M2+2 bits of information in the data packet according to a second constellation model, wherein the second constellation model includes 4*N2 constellation points, M2 is an integer greater than or equal to 1, and N2 and M2 satisfy the formula N2=2 M2 ;

[0044] The complex forms corresponding to the 4*N2 constellation points in the second constellation diagram model include the following:

[0045] a1e jθ ,a2e jθ ,…,a N2 e jθ ,

[0046] b1e j(θ+π / 2) ,b2e j(θ+π / 2) ,…,b N2 e j(θ+π / 2) ,

[0047] a1e j(θ+π) ,a2e j(θ+π) ,…,a N2 e j(θ+π) ,

[0048] b1e j(θ+3π / 2) ,b2e j(θ+3π / 2) ,…,b N2 e j(θ+3π / 2) ;

[0049] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N2 and

[0050] b1,b2,…,b N2 Are all positive numbers and satisfy: 0 <a1<a2<…<a N2 , 0 <b1<b2<…<b N2 ;

[0051] or,

[0052] The modulation symbol is obtained by modulating M3+3 bits of information in the data packet according to a third constellation model, wherein the third constellation model includes 8*N3 constellation points, M3 is an integer greater than or equal to 0, and N3 and M3 satisfy the formula N3=2 M3 ;

[0053] The complex forms corresponding to the 8*N3 constellation points in the third constellation diagram model include the following:

[0054] a1e jθ ,a2e jθ ,…,a N3 e jθ ,

[0055]

[0056]

[0057]

[0058] a1e j(θ+π) ,a2e j(θ+π) ,…,a N3 e j(θ+π) ,

[0059]

[0060]

[0061]

[0062] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N3 and b1,b2,…,b N3 Are all positive numbers and satisfy: 0 <a1<a2<…<a N3 , 0 <b1<b2<…<b N3 .

[0063] In a third aspect, an embodiment of the present application further provides a communication device, comprising: a memory, a processor, and a computer program stored in the memory and executable on the processor, wherein the processor implements the information transmission method described above when executing the computer program.

[0064] In a fourth aspect, an embodiment of the present application further provides a computer-readable storage medium storing computer-executable instructions, wherein the computer-executable instructions are used to execute the information transmission method described above.

[0065] In a fifth aspect, an embodiment of the present application further provides a computer program product, comprising a computer program or computer instructions, wherein the computer program or the computer instructions are stored in a computer-readable storage medium, and the processor of a computer device reads the computer program or the computer instructions from the computer-readable storage medium, and the processor executes the computer program or the computer instructions, so that the computer device performs the information transmission method as described above.

[0066] An embodiment of the present application includes: determining a first number of extremely sparse pilots, and then transmitting a data packet and the first number of extremely sparse pilots to a second communication node, wherein the first number is greater than or equal to 1, and the data packet at least contains a modulation symbol, and the modulation symbol is obtained by modulating M1+1 bits of information in the data packet according to a first constellation model, or by modulating M2+2 bits of information in the data packet according to a second constellation model, or by modulating M3+3 bits of information in the data packet according to a third constellation model, and M1 is an integer greater than or equal to 1, M2 is an integer greater than or equal to 1, and M3 is an integer greater than or equal to 0, that is, the first communication node transmits an extremely sparse pilot and a data packet containing the modulation symbol to the second communication node, so as to facilitate the transmission of the extremely sparse pilot and the data packet to the second communication node. The second communication node can estimate part of the information of the wireless channel from the extremely sparse pilot, and further extract the channel information from the modulation symbol, without having to estimate all the information of the wireless channel from the extremely sparse pilot, thereby reducing the pilot overhead of the first communication node, and then improving the accuracy of the channel estimation, thereby improving the demodulation performance of the second communication node, and realizing high-spectral-efficiency information transmission; and because M1 is an integer greater than or equal to 1, M2 is an integer greater than or equal to 1, and M3 is an integer greater than or equal to 0, the modulation symbol can be obtained by modulating multiple bits of information in the data packet according to the first constellation model, the second constellation model, or the third constellation model, that is, the modulation symbol can carry multiple bits of information, thereby realizing high-order modulation, and then improving the spectrum efficiency of information transmission. Therefore, the embodiment of the present application can support a large number of first communication nodes to realize high-spectral-efficiency information transmission. BRIEF DESCRIPTION OF THE DRAWINGS

[0067] Figure 1 This is a constellation diagram corresponding to the 64QAM modulation symbols provided in one embodiment of the present application;

[0068] Figure 2 This is a flowchart of an information transmission method provided by an embodiment of the present application;

[0069] Figure 3 1 is a schematic diagram of w mutually independent pilots provided by an embodiment of the present application;

[0070] Figure 4 is a flowchart of an information transmission method provided by another embodiment of the present application;

[0071] Figure 5 is a schematic diagram of a first constellation diagram model and a second constellation diagram model provided by an embodiment of the present application;

[0072] Figure 6 is a schematic diagram of a cross-shaped constellation diagram before and after channel rotation and scaling provided by an embodiment of the present application;

[0073] Figure 7 This is a schematic diagram of partitioning on a two-dimensional plane coordinate system provided by an embodiment of the present application;

[0074] Figure 8 is a schematic diagram of a cross-shaped constellation diagram provided by one embodiment of the present application;

[0075] Figure 9 is a schematic diagram of a cross-shaped constellation diagram provided by another embodiment of the present application;

[0076] Figure 10 is a schematic diagram of a cross-shaped constellation diagram provided by another embodiment of the present application;

[0077] Figure 11 is a schematic diagram of a cross-shaped constellation diagram provided by another embodiment of the present application;

[0078] Figure 12 is a schematic diagram of a cross-shaped constellation diagram provided by another embodiment of the present application;

[0079] Figure 13 is a schematic diagram of a cross-shaped constellation diagram provided by another embodiment of the present application;

[0080] Figure 14 is a schematic diagram of a cross-shaped constellation diagram provided by another embodiment of the present application;

[0081] Figure 15 is a schematic diagram of a cross-shaped constellation diagram provided by another embodiment of the present application;

[0082] Figure 16 is a schematic diagram of a cross-shaped constellation diagram provided by another embodiment of the present application;

[0083] Figure 17 is a schematic diagram of a cross-shaped constellation diagram provided by another embodiment of the present application;

[0084] Figure 18 is a schematic diagram of a cross-shaped constellation diagram provided by another embodiment of the present application;

[0085] Figure 19 is a schematic diagram of a PAM constellation diagram provided by one embodiment of the present application;

[0086] Figure 20 is a schematic diagram of a PAM constellation diagram provided by another embodiment of the present application;

[0087] Figure 21 is a schematic diagram of a third constellation diagram model provided by an embodiment of the present application;

[0088] Figure 22 is a schematic diagram of a third constellation diagram model provided by another embodiment of the present application;

[0089] Figure 23 This is a schematic diagram of defining physical resource blocks provided by an embodiment of the present application;

[0090] Figure 24 This is a schematic diagram of defining a demodulation reference signal provided by an embodiment of the present application;

[0091] Figure 25 This is a schematic diagram of distinguishing different reference signal ports by using OCC codes provided by an embodiment of the present application;

[0092] Figure 26 This is a schematic diagram of defining a demodulation reference signal using an OCC code, provided by an embodiment of the present application;

[0093] Figure 27 This is a schematic diagram of another method of defining a demodulation reference signal using an OCC code, provided by an embodiment of the present application;

[0094] Figure 28 This is a schematic diagram of another method of defining a demodulation reference signal using an OCC code, provided by an embodiment of the present application;

[0095] Figure 29 This is a schematic diagram of PRB-based transmission provided by an embodiment of the present application;

[0096] Figure 30 This is a schematic diagram of another method for defining a demodulation reference signal provided by an embodiment of the present application;

[0097] Figure 31 This is a schematic diagram of another method for defining a demodulation reference signal provided by an embodiment of the present application;

[0098] Figure 32 This is a schematic diagram of another method for defining a demodulation reference signal provided by an embodiment of the present application;

[0099] Figure 33 This is a schematic diagram of defining a reference signal provided by an embodiment of the present application;

[0100] Figure 34 This is a schematic diagram of another method for defining a reference signal provided by an embodiment of the present application;

[0101] Figure 35 This is a schematic diagram of another method for defining a reference signal provided by an embodiment of the present application;

[0102] Figure 36 This is a schematic diagram of generating a DMRS port provided by an embodiment of the present application;

[0103] Figure 37This is a schematic diagram of another method for defining a reference signal provided by an embodiment of the present application;

[0104] Figure 38 This is a schematic diagram of another method for defining a reference signal provided by an embodiment of the present application;

[0105] Figure 39 It is a structural diagram of a communication device provided by an embodiment of the present application. DETAILED DESCRIPTION

[0106] In order to make the purpose, technical solutions and advantages of this application more clear, the following further describes this application in detail with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are only used to explain this application and are not intended to limit this application.

[0107] It should be noted that although a logical order is shown in the flowchart, in some cases, the steps shown or described may be performed in an order different from that in the flowchart. In the description of the specification, claims and the above-mentioned drawings, the meaning of multiple (or multiple) is more than two, greater than, less than, exceed, etc. are understood to exclude the number itself, and above, below, within, etc. are understood to include the number itself. If there is a description of "first", "second", etc., it is only used for the purpose of distinguishing technical features, and cannot be understood as indicating or implying relative importance or implicitly indicating the number of the indicated technical features or implicitly indicating the order of the indicated technical features.

[0108] The present application provides an information transmission method, communication device and storage medium, wherein a first communication node can determine a first number of extremely sparse pilots, and then transmit a data packet and the first number of extremely sparse pilots to a second communication node, wherein the first number is greater than or equal to 1, and the data packet at least contains a modulation symbol, and the modulation symbol is obtained by modulating M1+1 bits of information in the data packet according to a first constellation diagram model, or by modulating M2+2 bits of information in the data packet according to a second constellation diagram model, or by modulating M3+3 bits of information in the data packet according to a third constellation diagram model, and M1 is an integer greater than or equal to 1, M2 is an integer greater than or equal to 1, and M3 is an integer greater than or equal to 0, that is, the first communication node transmits an extremely sparse pilot and the modulation symbol to the second communication node. Symbol data packet, so that the second communication node can estimate part of the information of the wireless channel from the extremely sparse pilot, and further extract the channel information from the modulation symbol, without having to estimate all the information of the wireless channel from the extremely sparse pilot, thereby reducing the pilot overhead of the first communication node, and then improving the accuracy of the channel estimation, thereby improving the demodulation performance of the second communication node, and realizing high-spectral-efficiency information transmission; and because M1 is an integer greater than or equal to 1, M2 is an integer greater than or equal to 1, and M3 is an integer greater than or equal to 0, the modulation symbol can be obtained by modulating multiple bits of information in the data packet according to the first constellation model, the second constellation model, or the third constellation model, that is, the modulation symbol can carry multiple bits of information, thereby realizing high-order modulation, and then improving the spectrum efficiency of information transmission. Therefore, the embodiment of the present application can support a large number of first communication nodes to realize high-spectral-efficiency information transmission.

[0109] It is worth noting that when a wireless communication system is connected to a large number of terminals, it needs to transmit information to these terminals. Furthermore, if the spectrum efficiency of information transmission for each terminal is required to be moderate, it is also necessary to increase the order of the modulation scheme to improve spectrum efficiency.

[0110] In the related art, the commonly used high-order modulation method is orthogonal amplitude modulation, such as 16QAM, 32QAM, 64QAM and 256QAM. The constellation points in the constellation diagram are relatively evenly distributed on the two-dimensional plane (i.e., the complex plane), so the two-dimensional signal space of the complex signal (i.e., the two-dimensional signal plane) can be more fully utilized. It can be understood that the communication signal can usually be represented by a complex number at the baseband, that is, the communication signal can be divided into an I-path signal and a Q-path signal, where the I-path signal is the real part and the Q-path signal is the imaginary part. Because the communication signal includes modulation symbols, the modulation symbols can also be represented by complex numbers, that is, one modulation symbol can be represented by a complex number. For example, the modulation symbol s can be represented as a+j*b, where j is an imaginary number, i.e., j=sqrt(-1); a is the real part of s, indicating that the modulation symbol is transmitted on the I-path, and b is the imaginary part of s, indicating that the modulation symbol is transmitted on the Q-path.

[0111] Taking the constellation diagram of the 16QAM method in the related art as an example, the constellation diagram includes 16 points, and the complex numbers corresponding to these 16 points include the following:

[0112] 3+3j,3+j,3-j,3-3j,

[0113] 1+3j,1+j,1-j,1-3j,

[0114] -1+3j,-1+j,-1-j,-1-3j,

[0115] -3+3j,-3+j,-3-j,-3-3j

[0116] It can be seen from the complex numbers corresponding to the 16 points that in the two-dimensional plane (also called the complex plane, or the complex signal space, or the two-dimensional signal space) with the real part value range of -3 to 3 and the imaginary part value range of -3 to 3, the 16QAM constellation points are distributed relatively evenly. It can be understood that the complex plane is equivalent to the two-dimensional plane, so the complex plane or the two-dimensional plane can also be called the two-dimensional complex plane, where the real part of the complex number is equivalent to the x-coordinate of the two-dimensional plane, and the imaginary part of the complex number is equivalent to the y-coordinate of the two-dimensional plane. Therefore, complex numbers can also be represented by points on the two-dimensional plane. For example, the complex number a+j*b can be represented by the coordinates (a, b) on the two-dimensional plane, where the coordinates (a, b) indicate that the x-coordinate on the two-dimensional plane is a and the y-coordinate is b. Therefore, in addition to being represented by 16 complex numbers, the 16 points in the 16QAM constellation diagram can also be represented by 16 two-dimensional coordinates on the two-dimensional plane, where the 16 two-dimensional coordinates include the following:

[0117] (3,3),(3,1),(3,-1),(3,-3),

[0118] (1,3),(1,1),(1,-1),(1,-3),

[0119] (-1,3),(-1,1),(-1,-1),(-1,-3),

[0120] (-3,3),(-3,1),(-3,-1),(-3,-3)

[0121] In this embodiment, when it is necessary to perform power normalization processing on the entire constellation diagram, the entire constellation diagram can be multiplied by a normalization factor (or scaling factor). For example, the 16 complex numbers corresponding to the 16QAM modulation mode are all multiplied by the same normalization factor 1 / sqrt(40). The complex numbers corresponding to the 16 points in the 16QAM constellation diagram after power normalization processing include the following:

[0122] 1 / sqrt(40)*3+3j,3+j,3-j,3-3j,1+3j,1+j,1-j,1-3j,-1+3j,-1+j,-1-j,-1-3j,-3+3j,-3+j,-3-j,-3-3j]

[0123] The coordinates of the 16 points in the power-normalized 16QAM constellation diagram can be obtained by multiplying the 16 two-dimensional coordinates listed above by 1 / sqrt(40), that is, multiplying the x-coordinate and y-coordinate of each two-dimensional coordinate by 1 / sqrt(40).

[0124] It is understandable that power normalization only reduces the overall size of the constellation diagram, and the constellation points in the reduced constellation diagram are still evenly distributed.

[0125] For other high-order modulation methods, such as 32QAM, 64QAM, 256QAM, etc., similar to the 16QAM modulation method, the constellation points of their constellation diagrams are evenly distributed on a two-dimensional plane. Therefore, the high-order modulation methods in the related art can fully utilize the two-dimensional signal space of the complex signal. Moreover, the demodulation methods corresponding to these high-order modulation methods are not only simple but also can guarantee performance. Therefore, these high-order modulation methods can relatively simply and efficiently approach the performance limit of transmission, namely the Shannon limit. Therefore, in scenarios with certain requirements for spectrum efficiency, these high-order modulation methods can be widely used. However, these high-order modulation methods require relatively accurate channel estimation to ensure performance. If the channel estimation error is large, the constellation diagram will be distorted, that is, rotated and scaled, during demodulation by the base station (or access point). At this time, the demodulation performance will degrade.

[0126] Specifically, taking the transmission of modulation symbols via orthogonal frequency division multiplexing (OFDM) (i.e., using OFDM subcarriers to transmit modulation symbols) as an example, after passing through a multipath channel or a frequency-selective channel, the modulation symbols carried on the OFDM subcarriers will be weighted with a complex weight (i.e., the frequency-selective channel will cause the modulation symbols carried on the subcarriers to be distorted); or, if there is a large synchronization error between the sender and receiver (i.e., the first communication node and the second communication node), the timing deviation (i.e., time deviation) and frequency deviation (i.e., frequency deviation) will also cause the modulation symbols on the subcarriers to be weighted with a complex weight, i.e., the synchronization error will cause the modulation symbols to be distorted. Similarly, in high-speed mobile scenarios or satellite communication scenarios, the Doppler effect will also cause the modulation symbols on the subcarriers to be weighted with a complex weight, i.e., the synchronization error will cause the modulation symbols to be distorted. Because the rotation and scaling of modulation symbols (i.e., the rotation and scaling) vary rapidly in scenarios with large synchronization errors, high-speed mobility (such as in satellite communications), or high phase noise, pilot signals with very short time intervals are required to accurately estimate the rotation and scaling of modulation symbols between pilot signals. However, this increases pilot signal overhead, ultimately reducing transmission spectral efficiency. Furthermore, if the temporal density of pilot signals does not meet the requirements, it is also difficult to accurately estimate the rotation and scaling of modulation symbols, thus degrading demodulation performance.

[0127] Furthermore, these distortions occurring on the modulation symbols will be superimposed. Taking the transmission of the modulation symbol s via OFDM as an example, assuming that the frequency-selective channel causes the complex weight of the modulation symbol s on the OFDM subcarrier to be g1, and the time-frequency or frequency offset causes the complex weight of the modulation symbol to be g2. If the above-mentioned frequency-selective channel and the above-mentioned synchronization error exist at the same time, it is equivalent to weighting the modulation symbol with a weight value h, where h = g1*g2, that is, the received modulation symbol is y = h*s+n = g1*g2*s+n, where n is additive white Gaussian noise (AWGN). If the receiving side (i.e., the second communication node) cannot remove the distortion on the modulation symbol, that is, cannot equalize the weight value h of the modulation symbol, then the modulation symbol will be rotated and scaled. The modulation symbols that have undergone slight rotation and scaling will also seriously restrict the performance of high-order modulation methods, such as Figure 1 As shown, each small dot in the figure corresponds to a modulation symbol, where Figure 1 The constellation diagram corresponding to the coordinate system on the left is the constellation diagram corresponding to the standard 64QAM modulation symbol; Figure 1The constellation diagram corresponding to the coordinate system on the right is the constellation diagram corresponding to the 64QAM modulation symbol weighted by a weight value (i.e., a rotation and scaling amount), that is, the constellation diagram corresponding to the 64QAM modulation symbol that has undergone channel distortion. Figure 1 If the constellation corresponding to the coordinate system on the right is demodulated, even if the AWGN on the receiving side is small, the demodulation performance will be affected. Therefore, in traditional high-spectral-efficiency scenarios, pilot signals are usually used to estimate the complex weights (i.e., distortion) of the modulation symbols. That is, h in the received modulation symbol y = h*s+n = g1*g2*s+n is estimated, and then the weighted value is equalized, that is, y is divided by h, that is, y / h = s+n / h, to obtain a constellation s+n′ that is free of distortion and only affected by additive white Gaussian noise, thereby achieving better demodulation performance, where n′ = n / h. However, for scenarios such as massive terminals in a disconnected state (i.e., the terminals are not connected to the wireless communication system) and directly transmitting information with the wireless communication system, as well as scenarios where massive terminals transmit information based on semi-persistent scheduling (SPS), it is difficult to accurately estimate the complex weights (i.e., distortion) of the modulation symbols through pilot signals. Therefore, the performance of high-order modulation schemes will be severely restricted.

[0128] In addition, in scenarios where a wireless communication system is connected to a large number of terminals, the massive terminals transmitting information with the system will increase the pilot overhead at the terminals, which will make it difficult to ensure the accuracy of channel estimation and therefore limit the demodulation performance of the base station (or access point).

[0129] The increase in pilot overhead caused by using a traditional pilot scheme to implement information transmission between a first communication node and a second communication node is described in detail below.

[0130] To save power, the terminal generally does not establish a connection with the system when no information transmission is required (i.e., the terminal is not connected to the system, or the terminal is disconnected from the system), that is, the terminal is in a disconnected state (wherein, Non Connected state, Non RRC Connected state, Connectionless state, Connection-free state, or Disconnected state, etc. can all represent a disconnected state). It can be understood that the idle state or inactive state can be considered equivalent to the disconnected state, or the idle state or inactive state can also be considered a type of disconnected state.

[0131] When the terminal is originally in a disconnected state (i.e., it has not yet entered a connected state, or has not yet established a connection with the system), if the uplink information transmission scheme in the relevant technology is used, in order to transmit information, the terminal must establish a connection with the system before transmission. After entering the connected state (also called the active state), the terminal can further apply for uplink transmission resources from the system (such as a base station or access point), and can only transmit information after obtaining resource authorization or resource scheduling from the system. It can be seen that in order to complete a traditional uplink information transmission, the terminal needs to complete many operations in advance, which will undoubtedly increase the power consumption generated by the terminal and the signaling overhead of the system.

[0132] On the contrary, if the terminal transmits information with the system in a disconnected state, then before the information is transmitted, the terminal does not need to establish a connection, nor does it need to apply for dedicated transmission resources from the base station (or access point). That is, the terminal in a connectionless state does not need to notify the base station (or access point) before information transmission, but instead autonomously transmits information to the base station directly on a preset public transmission resource. Therefore, information transmission in a connectionless state can reduce the complexity of information transmission, reduce the power consumption generated by the terminal during information transmission, and the transmission delay of data to the base station (or access point), and also saves the signaling overhead required for information transmission.

[0133] However, in the case of information transmission in a connectionless state, the first communication node (such as a terminal) needs to autonomously select a pilot (or reference signal) from a preset pilot set. However, this leads to a problem. Since there is no central node to coordinate the pilots sent by different first communication nodes, different first communication nodes autonomously select pilots from a preset pilot set with a limited number of pilots. The selected pilots may be the same, which may cause pilot collisions. In scenarios with high overload (i.e., many first communication nodes are sending data packets to the same second communication node), the probability of pilot collisions is very high. Once the pilots of different first communication nodes collide, it is difficult for the second communication node to separate multiple first communication nodes through the pilots.

[0134] Therefore, to reduce the number of pilot collisions, more pilots need to be defined. This means that the number of pilots in the preset pilot set should be as large as possible. However, increasing the number of pilots also increases the pilot overhead. Furthermore, if traditional pilot schemes are used, each pilot must be used to estimate the channel and time-frequency offset to perform coherent demodulation of the modulation symbols. Therefore, each pilot must have a signal across the entire transmission bandwidth and time. In other words, each pilot must be distributed across the entire transmission bandwidth and time. This ensures that channel information (such as wireless multipath channels, also known as frequency-selective channels) and frequency offset within the transmission time can be estimated. Therefore, to ensure the transmission performance of information transmission in a connectionless state, using traditional pilot schemes will result in an exponential increase in pilot overhead and a significant increase in detection complexity.

[0135] Furthermore, in the related art, there is a method for uplink information transmission, namely semi-persistent scheduling, which aims to reduce the physical control signaling overhead and latency of transmission and is very suitable for periodic services. However, if the SPS method is used to implement information transmission for a large number of terminals, in order to improve the utilization of periodic reserved resources, one SPS resource can be reserved for shared use by multiple terminals. This requires defining a large number of pilots within a certain time-frequency resource. Similarly, under certain pilot resources, extremely sparse pilots can maximize the number of available pilots, and thus maximize the number of terminals using the same SPS resource. Therefore, extremely sparse pilots are very suitable for information transmission scenarios based on semi-persistent scheduling for massive terminals.

[0136] In response to the above situation, the present application proposes to support information transmission by massive terminals at higher spectrum efficiency by combining extremely sparse pilots and modulation methods.

[0137] It is understandable that the scheme based on extremely sparse pilots can allow the system to support more terminal access. Therefore, the scheme based on extremely sparse pilots is very suitable for large-connection scenarios, such as scenarios where a large number of terminals directly transmit information in a disconnected state, and scenarios where a large number of users transmit information based on SPS. However, the scheme based on extremely sparse pilots requires that the receiving side (i.e., the second communication node) be able to perform channel estimation based on the characteristics of the modulation symbols themselves, while the constellation diagram of the traditional high-order modulation method is too dense, which is not conducive to the receiving side extracting channel information through modulation symbols. Based on this, the present application proposes an information transmission method that can not only support high spectral effect application scenarios, but also reduce the complexity of the receiving side extracting channel information through modulation symbols, and improve the accuracy of the channel information extracted by the receiving side through modulation symbols.

[0138] Reference Figure 2 , Figure 2This is a flowchart of an information transmission method provided by an embodiment of the present application. The information transmission method is applied to a first communication node. The information transmission method may include but is not limited to step S110 and step S120.

[0139] Step S110: Determine a first number of extremely sparse pilots.

[0140] Step S120: Transmit the data packet and the first number of extremely sparse pilots to the second communication node.

[0141] The first number is greater than or equal to 1, and the data packet at least includes a modulation symbol.

[0142] Furthermore, the modulation symbol is obtained by modulating M1+1 bits of information in the data packet according to the first constellation model, the first constellation model includes 2*N1 constellation points, M1 is an integer greater than or equal to 1, and N1 and M1 satisfy the formula N1=2 M1 ;

[0143] The complex forms corresponding to the 2*N1 constellation points in the first constellation diagram model include the following:

[0144] a1e jθ ,a2e jθ ,…,a N1 e jθ ,

[0145] a1e j(θ+π) ,a2e j(θ+π) ,…,a N1 e j(θ+π)

[0146] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N1 Are all positive numbers and satisfy: 0 <a1<a2<…<a N1 ;

[0147] or,

[0148] The modulation symbol is obtained by modulating the M2+2 bits of information in the data packet according to the second constellation model. The second constellation model includes 4*N2 constellation points, M2 is an integer greater than or equal to 1, and N2 and M2 satisfy the formula N2=2 M2 ;

[0149] The complex forms corresponding to the 4*N2 constellation points in the second constellation diagram model include the following:

[0150] a1e jθ ,a2e jθ ,…,a N2 ejθ ,

[0151] b1e j(θ+π / 2) ,b2e j(θ+π / 2) ,…,e N2 e j(θ+π / 2) ,

[0152] a1e j(θ+π) ,a2e j(θ+π) ,…,a N2 e j(θ+π) ,

[0153] b1e j(θ+3π / 2) ,b2e j(θ+3π / 2) ,…,b N2 e j(θ+3π / 2) ;

[0154] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N2 and b1,b2,…,b N2 Are all positive numbers and satisfy: 0 <a1<a2<…<a N2 , 0 <b1<b2<…<b N2 ;

[0155] or,

[0156] The modulation symbol is obtained by modulating the M3+3 bits of information in the data packet according to the third constellation model. The third constellation model contains 8*N3 constellation points, M3 is an integer greater than or equal to 0, and N3 and M3 satisfy the formula N3=2 M3 ;

[0157] The complex forms corresponding to the 8*N3 constellation points in the third constellation diagram model include the following:

[0158] a1e jθ ,a2e jθ ,…,a N3 e jθ ,

[0159]

[0160]

[0161]

[0162] a1e j(θ+π) ,a2e j(θ+π) ,…,a N3 e j(θ+π) ,

[0163]

[0164]

[0165]

[0166] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N3 and b1,b2,…,b N3 Are all positive numbers and satisfy: 0 <a1<a2<…<a N3 , 0 <b1<b2<…<b N3 .

[0167] In this embodiment, by adopting the information transmission method including the above-mentioned steps S110 and S120, a first number of extremely sparse pilots can be determined, and then the data packet and the first number of extremely sparse pilots are transmitted to the second communication node together, wherein the first number is greater than or equal to 1, and the data packet at least includes a modulation symbol, and the modulation symbol is obtained by modulating M1+1 bits of information in the data packet according to the first constellation diagram model, or by modulating M2+2 bits of information in the data packet according to the second constellation diagram model, or by modulating M3+3 bits of information in the data packet according to the third constellation diagram model, and M1 is an integer greater than or equal to 1, M2 is an integer greater than or equal to 1, and M3 is an integer greater than or equal to 0, that is, the first communication node transmits the extremely sparse pilots and the first number of extremely sparse pilots to the second communication node. The data packet of the modulation symbol is so that the second communication node can estimate part of the information of the wireless channel from the extremely sparse pilot, and further extract the channel information from the modulation symbol, without having to estimate all the information of the wireless channel from the extremely sparse pilot, thereby reducing the pilot overhead of the first communication node, and then improving the accuracy of the channel estimation, thereby improving the demodulation performance of the second communication node, and realizing high-spectral-efficiency information transmission; and because M1 is an integer greater than or equal to 1, M2 is an integer greater than or equal to 1, and M3 is an integer greater than or equal to 0, the modulation symbol can be obtained by modulating multiple bits of information in the data packet according to the first constellation model, the second constellation model, or the third constellation model, that is, the modulation symbol can carry multiple bits of information, thereby realizing high-order modulation, and then improving the spectrum efficiency of information transmission. Therefore, the embodiment of the present application can support a large number of first communication nodes to realize high-spectral-efficiency information transmission.

[0168] It is understandable that the pilot can be called a pilot signal, or a reference signal (RS), or a demodulation reference signal, or a preamble, and in terms of form, the pilot is usually a sequence or a string of symbols, so the pilot is also called a pilot sequence.

[0169] In a feasible implementation manner, each extremely sparse pilot includes a second number of non-zero value symbols, wherein the second number is greater than 0 and less than 5. The second number of non-zero value symbols is carried on a third number of resource elements (REs) adjacent in the time-frequency domain, or on a third number of symbols in chronological order, or on a third number of resource elements on adjacent subcarriers in the frequency domain, wherein the third number is equal to the second number (i.e., the third number is greater than 0 and less than 5). It is understandable that each extremely sparse pilot has only one reference signal element (RSE), and the number of non-zero value symbols contained in the RSE is the second number. It is understandable that, for OFDM, one resource element (RE) can carry one symbol. In addition, if the second number of non-zero value symbols are carried on adjacent REs, it is equivalent to the second number of symbols being carried on adjacent time-frequency resources. Alternatively, for OFDM, if the second number of non-zero value symbols are carried on adjacent time-frequency resources, it is equivalent to the second number of non-zero value symbols being carried on adjacent REs.

[0170] In a feasible implementation manner, the value of the second number is 4, the second number of non-zero value symbols constitutes a non-zero value symbol group [p1, p2, p3, p4], and the values ​​of [p1, p2, p3, p4] include at least the various situations as shown in Table 1, wherein different serial numbers in Table 1 correspond to different situations.

[0171] Table 1

[0172] Serial number p1 p2 p3 p4 Serial number p1 p2 p3 p4 1 1 1 1 1 33 1 1 1 j 2 1 1 -1 -1 34 1 1 -1 -j 3 1 -1 1 -1 35 1 -1 1 -j 4 1 -1 -1 1 36 1 -1 -1 j 5 1 1 j -j 37 1 1 j 1 6 1 1 -j j 38 1 1 -j -1 7 1 -1 j j 39 1 -1 j -1 8 1 -1 -j -j 40 1 -1 -j 1 9 1 j 1 -j 41 1 j 1 1 10 1 j -1 j 42 1 j -1 -1 11 1 -j 1 j 43 1 -j 1 -1 12 1 -j -1 -j 44 1 -j -1 1 13 1 j j -1 45 1 j j -j 14 1 j -j 1 46 1 j -j j 15 1 -j j 1 47 1 -j j j 16 1 -j -j -1 48 1 -j -j -j 17 1 1 1 -1 49 1 1 1 -j 18 1 1 -1 1 50 1 1 -1 j 19 1 -1 1 1 51 1 -1 1 j 20 1 -1 -1 -1 52 1 -1 -1 -j 21 1 1 j j 53 1 1 j -1 22 1 1 -j -j 54 1 1 -j 1 23 1 -1 j -j 55 1 -1 j 1 24 1 -1 -j j 56 1 -1 -j -1 25 1 j 1 j 57 1 j 1 -1 26 1 j -1 -j 58 1 j -1 1 27 1 -j 1 -j 59 1 -j 1 1 28 1 -j -1 j 60 1 -j -1 -1 29 1 j j 1 61 1 j j j 30 1 j -j -1 62 1 j -j -j 31 1 -j j -1 63 1 -j j -j 32 1 -j -j 1 64 1 -j -j j

[0173] In a feasible implementation manner, the value of the second number is 1, that is, a non-zero value symbol; or, the value of the second number is 2, the second number of non-zero value symbols constitutes a non-zero value symbol pair [p1, p2], and the value of [p1, p2] is [a1, a2] or [b1, b2], wherein [a1, a2] and [b1, b2] are orthogonal, that is, a1′*b1+a2′*b2=0; or, the value of the second number is 2, the second number of non-zero value symbols constitutes a non The zero-valued symbol pair [p1, p2], the values ​​of [p1, p2] include at least [p1, p2] = [1, 1]; [p1, p2] = [1, -1]; [p1, p2] = ] 1, j]; [p1, p2] = [1, -j] and the like; or, the second number has a value of 4, the second number of non-zero-valued symbols constitutes a non-zero-valued symbol group [p1, p2, p3, p4], and the values ​​of [p1, p2, p3, p4] are [a1, a2, a3 ,a4], [b1,b2,b3,b4], [c1,c2,c3,c4] or [d1,d2,d3,d4], where [a1,a2,a3,a4], [b1,b2,b3,b4], [c1,c2,c3,c4] and [d1,d2,d3,d4] are orthogonal to each other, i.e. [a1,a2,a3,a4], [b1,b2,b3,b4], [c1,c2,c3,c4] and [d1,d2,d3,d4] 2, d3, d4] are mutually orthogonal. Specifically, [a1, a2, a3, a4] and [b1, b2, b3, b4] are mutually orthogonal, that is, a1′*b1+a2′*b2+a3′*b3+a4′*b4=0; [a1, a2, a3, a4] and [c1, c2, c3, c4] are mutually orthogonal, that is, a1′*c1+a2′*c2+a3′*c3+a4′*c4=0, and so on. No further details are given here.

[0174] In a feasible implementation manner, the symbol length of each extremely sparse pilot is greater than 24, that is, the total number of non-zero value symbols and zero value symbols of each extremely sparse pilot is greater than 24, which is not specifically limited here.

[0175] A feasible implementation method is that when the value of the first number is greater than or equal to 2, the first number of extremely sparse pilots are independent of each other, that is, the first number of extremely sparse pilots are not associated or related, wherein the value of the first number can be greater than or equal to 1, that is, the value of the first number can be 1, 2 or other values, and no specific limitation is made here. Among them, the technology of including 2 or more pilots in one transmission and the pilots are not associated or independent of each other is called independent multi-pilot technology, and the multiple independent pilots are called independent multi-pilots. Figure 3As shown, w extremely sparse pilots are included in one transmission, where the w extremely sparse pilots are respectively represented as P1, P2, ..., Pw, w can be a positive integer greater than 2, and the data packet contains information about the w extremely sparse pilots. For example, the data packet contains the index numbers of the w extremely sparse pilots (that is, the index numbers of the extremely sparse pilots in the preset pilot set). In this way, once the data packet of a terminal is successfully decoded, the information of all extremely sparse pilots used by the terminal in this information transmission can be determined, so that interference with the pilot signal can be eliminated.

[0176] It is understandable that the information transmission between the first communication node and the second communication node can adopt independent multi-pilot technology. In this way, under the same pilot overhead, the probability of simultaneous collision of independent multi-pilots of different first communication nodes will be smaller than the probability of collision of traditional single pilots. Therefore, in a transmission scenario of a competitive connectionless state (or a competitive scheduling-free mode), independent multi-pilot technology can be adopted to support more first communication nodes for information transmission. Furthermore, independent multi-pilot technology and extremely sparse pilot technology can be combined, that is, multiple independent and extremely sparse pilots are adopted to further reduce the probability of pilot collision and further increase the number of first communication nodes connected.

[0177] In one embodiment, when the second communication node is a base station, through an iterative receiver, the base station can demodulate the corresponding first communication node in each round through multiple non-colliding (i.e., independent of each other) extremely sparse pilots, and then reconstruct the data packet and extremely sparse pilot of the first communication node, and eliminate the data packet and extremely sparse pilot corresponding to the first communication node from the received signal. This iteration is repeated until all decomposable first communication nodes are demodulated to reduce the probability of pilot collision and further increase the number of accessed first communication nodes.

[0178] In one embodiment, when the value of the first number is greater than or equal to 2, the first number of extremely sparse pilots may be determined according to information in the data packet.

[0179] In another embodiment, when the value of the first number is greater than or equal to 2, the first number of extremely sparse pilots can be determined based on one or more bits of information in the data packet. For example, an extremely sparse pilot can be determined based on one bit of information in the data packet; for another example, an extremely sparse pilot can be determined based on two bits of information in the data packet; for another example, both extremely sparse pilots are determined based on multiple bits of information in the data packet, and so on. The embodiment of the present application does not limit the first number and the number of bit information.

[0180] In another embodiment, when the value of the first number is greater than or equal to 2, each extremely sparse pilot is determined from a preset pilot set based on a fourth number of bits in the data packet, where the preset pilot set includes a fifth number of pilots, and the fourth number and the fifth number form a logarithmic function relationship, where the logarithmic function is a logarithmic function with a base of 2. For example, assuming that the fifth number is D, the fourth number is log2(D), without specific limitation herein. It is understood that the fifth number can be 64, 128, or more, without specific limitation herein.

[0181] In a feasible implementation mode, when the modulation symbols are modulated according to the first constellation model, a1, a2, ..., a N1 can be expressed by the following formula, namely

[0182] a n =(2n-1+Δ)d;

[0183] Among them, the value of n includes 1, 2, ..., N1, that is, a n It can be a1, a2, a3, or a N1 Etc. d is a positive real number, Δ is a real number greater than or equal to 0, such that a1, a2, ..., a N1 Form an arithmetic progression.

[0184] Furthermore, when the value of Δ is 0 and the value of d is 1, so that a n Satisfy a n =2n-1; when Δ is 1 and d is 1 / 2, then a n Satisfy a n =n; when Δ is 3 and d is 1 / 2, then a n Satisfy a n =n+1.

[0185] Alternatively, the value of Δ can be At this time, when the value of d is 1, making a n satisfy When the value of d is 1 / 2, so that a n satisfy

[0186] In a feasible implementation mode, when the modulation symbols are modulated according to the second constellation model, a1, a2, ..., a N2 Both can be expressed by the following formula:

[0187] a n =(2n-1+Δ)d;

[0188] b1,b2,…,b N2 Both can be expressed by the following formula:

[0189] b n =a n +β;

[0190] Among them, the value of n includes 1, 2, ..., N2, that is, a n It can be a1, a2, a3, or a N2 Etc. Similarly, b n It can be b1, b2, b3 or b N2 Etc. d is a positive real number, Δ and β are both real numbers greater than or equal to 0, such that a1, a2,…, a N2 Construct an arithmetic progression, b1, b2,…, b N2 Form an arithmetic progression.

[0191] Furthermore, when the value of Δ is 0 and the value of d is 1, so that a n Satisfy a n =2n-1; when Δ is 1 and d is 1 / 2, then a n Satisfy a n =n; when Δ is 3 and d is 1 / 2, then a n Satisfy a n =n+1.

[0192] Alternatively, the value of Δ can be At this time, when the value of d is 1, making a n satisfy When the value of d is 1 / 2, so that a n satisfy

[0193] In a feasible implementation mode, when the modulation symbols are modulated according to the third constellation model, a1, a2, ..., a N3 Both can be expressed by the following formula:

[0194] a n =(2n-1+Δ)d;

[0195] b1,b2,…,b N3 Both can be expressed by the following formula:

[0196] b n =a n +β;

[0197] Among them, the value of n includes 1, 2, ..., N3, that is, a n It can be a1, a2, a3, or a N3 Etc. Similarly, b nIt can be b1, b2, b3, or b N3 Etc. d is a positive real number, Δ and β are both real numbers greater than or equal to 0, such that a1, a2,…, a N3 Construct an arithmetic progression, b1, b2,…, b N3 Form an arithmetic progression.

[0198] Furthermore, when the value of Δ is 0 and the value of d is 1, so that a n Satisfy a n =2n-1; when Δ is 1 and d is 1 / 2, then a n Satisfy a n =n; when Δ is 3 and d is 1 / 2, then a n Satisfy a n =n+1.

[0199] Alternatively, the value of Δ can be At this time, when the value of d is 1, making a n satisfy When the value of d is 1 / 2, so that a n satisfy

[0200] In a feasible implementation manner, when the modulation symbol is modulated according to the second constellation model or the third constellation model, β is equal to 0.

[0201] In a feasible implementation manner, when the modulation symbol is modulated according to the third constellation model, β is greater than 0.

[0202] In a feasible implementation manner, when the modulation symbol is modulated according to the first constellation diagram model, the value of d is a value that makes the average power of the modulation symbol obtained by modulation using the first constellation diagram model equal to 1, that is, the value of d makes the mean of the square of the modulus of the constellation points in the first constellation diagram model is 1, that is, the value of d makes the average power of the first constellation diagram model is 1, and no specific limitation is given here.

[0203] In a feasible implementation manner, when the modulation symbol is modulated according to the second constellation diagram model, the value of d is a value that makes the average power of the modulation symbol obtained by modulation using the second constellation diagram model equal to 1, that is, the value of d makes the mean of the square of the modulus of the constellation points in the second constellation diagram model is 1, that is, the value of d makes the average power of the second constellation diagram model is 1, and no specific limitation is given here.

[0204] In a feasible implementation manner, when the modulation symbol is modulated according to the third constellation model, the value of d is a value that makes the average power of the modulation symbol obtained by modulation using the third constellation model equal to 1, that is, the value of d makes the mean of the square of the modulus of the constellation points in the third constellation model is 1, that is, the value of d makes the average power of the third constellation model is 1, and no specific limitation is given here.

[0205] In a feasible implementation manner, the value of θ may be 0; or, the value of θ may be π / 4, that is, satisfying the formula θ=π / 4; or, the value of θ satisfies the formula θ=π / 8, and no specific limitation is given here.

[0206] in addition, Figure 4 Another embodiment of the present application provides an information transmission method, which is applied to the second communication node. The information transmission method may include but is not limited to step S210.

[0207] Step S210: Receive a data packet and a first number of extremely sparse pilots sent by a first communication node.

[0208] Among them, the first number is greater than or equal to 1, the data packet contains at least a modulation symbol, and the modulation symbol is obtained by modulating M1+1 bits of information in the data packet according to the first constellation model. The first constellation model includes 2*N1 constellation points, M1 is an integer greater than or equal to 1, and N1 and M1 satisfy the formula N1=2 M1 ;

[0209] The complex forms corresponding to the 2*N1 constellation points in the first constellation diagram model include the following:

[0210] a1e jθ ,a2e jθ ,…,a N1 e jθ ,

[0211] a1e j(θ+π) ,a2e j(θ+π) ,…,a N1 e j(θ+π) ;

[0212] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N1 Are all positive numbers and satisfy: 0 <a1<a2<…<a N1 ;

[0213] Alternatively, the modulation symbol is obtained by modulating M2+2 bits of information in the data packet according to the second constellation model, the second constellation model includes 4*N2 constellation points, M2 is an integer greater than or equal to 1, and N2 and M2 satisfy the formula N2=2 M2 ;

[0214] The complex forms corresponding to the 4*N2 constellation points in the second constellation diagram model include the following:

[0215] a1e jθ ,a2e jθ ,…,a N2 e jθ ,

[0216] b1e j(θ+π / 2) ,b2e j(θ+π / 2) ,…,b N2 e j(θ+π / 2) ,

[0217] a1e j(θ+π) ,a2e j(θ+π) ,…,a N2 e j(θ+π) ,

[0218] b1e j(θ+3π / 2) ,b2e j(θ+3π / 2) ,…,b N2 e j(θ+3π / 2) ;

[0219] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N2 and b1,b2,…,b N2 Are all positive numbers and satisfy: 0 <a1<a2<…<a N2 , 0 <b1<b2<…<b N2 ;

[0220] Alternatively, the modulation symbol is obtained by modulating M3+3 bits of information in the data packet according to a third constellation model, the third constellation model includes 8*N3 constellation points, M3 is an integer greater than or equal to 0, and N3 and M3 satisfy the formula N3=2 M3 ;

[0221] The complex forms corresponding to the 8*N3 constellation points in the third constellation diagram model include the following:

[0222] a1e jθ ,a2e jθ ,…,a N3 e jθ ,

[0223]

[0224]

[0225]

[0226] a1e j(θ+π) ,a2e j(θ+π) ,…,a N3 e j(θ+π) ,

[0227]

[0228]

[0229]

[0230] π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N3 and b1,b2,…,b N3 Are all positive numbers and satisfy: 0 <a1<a2<…<a N3 , 0 <b1<b2<…<b N3 .

[0231] In this embodiment, by adopting the information transmission method including the above-mentioned step S210, the second communication node can receive the data packet and the first number of extremely sparse pilots sent by the first communication node, wherein the first number is greater than or equal to 1, and the data packet at least includes a modulation symbol, and the modulation symbol is obtained by modulating M1+1 bits of information in the data packet according to the first constellation diagram model, or by modulating M2+2 bits of information in the data packet according to the second constellation diagram model, or by modulating M3+3 bits of information in the data packet according to the third constellation diagram model, and M1 is an integer greater than or equal to 1, M2 is an integer greater than or equal to 1, and M3 is an integer greater than or equal to 0, that is, the second communication node can receive the data packet sent by the first communication node. Part of the information of the wireless channel is estimated from the extremely sparse pilot, and the channel information is further extracted from the modulation symbol, without estimating all the information of the wireless channel from the extremely sparse pilot, thereby reducing the pilot overhead of the first communication node, and further improving the accuracy of the channel estimation, thereby improving the demodulation performance of the second communication node, and realizing high-spectral-efficiency information transmission; and because M1 is an integer greater than or equal to 1, M2 is an integer greater than or equal to 1, and M3 is an integer greater than or equal to 0, the modulation symbol can be obtained by modulating multiple bits of information in the data packet according to the first constellation model, the second constellation model, or the third constellation model, that is, the modulation symbol can carry multiple bits of information, thereby realizing high-order modulation, and thus improving the spectrum efficiency of information transmission. Therefore, the embodiment of the present application can support a large number of first communication nodes to realize high-spectral-efficiency information transmission.

[0232] It is understandable that the pilot can be called a pilot signal, or a reference signal (RS), or a demodulation reference signal, or a preamble, and in terms of form, the pilot is usually a sequence or a string of symbols, so the pilot is also called a pilot sequence.

[0233] In a feasible implementation manner, each extremely sparse pilot includes a second number of non-zero value symbols, wherein the second number is greater than 0 and less than 5. The second number of non-zero value symbols is carried on a third number of resource elements (REs) adjacent in the time-frequency domain, or on a third number of symbols in chronological order, or on a third number of resource elements on adjacent subcarriers in the frequency domain, wherein the third number is equal to the second number (i.e., the third number is greater than 0 and less than 5). It is understandable that each extremely sparse pilot has only one reference signal element (RSE), and the number of non-zero value symbols contained in the RSE is the second number. It is understandable that, for OFDM, one resource element (RE) can carry one symbol. In addition, if the second number of non-zero value symbols are carried on adjacent REs, it is equivalent to the second number of symbols being carried on adjacent time-frequency resources. Alternatively, for OFDM, if the second number of non-zero value symbols are carried on adjacent time-frequency resources, it is equivalent to the second number of non-zero value symbols being carried on adjacent REs.

[0234] In a feasible implementation manner, the value of the second number is 1, that is, a non-zero value symbol; or, the value of the second number is 2, the second number of non-zero value symbols constitutes a non-zero value symbol pair [p1, p2], and the value of [p1, p2] is [a1, a2] or [b1, b2], wherein [a1, a2] and [b1, b2] are orthogonal, that is, a1′*b1+a2′*b2=0; or, the value of the second number is 2, the second number of non-zero value symbols constitutes a non The zero-valued symbol pair [p1, p2], the values ​​of [p1, p2] include at least [p1, p2] = [1, 1]; [p1, p2] = [1, -1]; [p1, p2] = [1, j]; [p1, p2] = [1, -j] and the like; or, the second number has a value of 4, the second number of non-zero-valued symbols constitutes a non-zero-valued symbol group [p1, p2, p3, p4], and the values ​​of [p1, p2, p3, p4] are [a1, a2, a3 ,a4], [b1,b2,b3,b4], [c1,c2,c3,c4] or [d1,d2,d3,d4], where [a1,a2,a3,a4], [b1,b2,b3,b4], [c1,c2,c3,c4] and [d1,d2,d3,d4] are orthogonal to each other, i.e. [a1,a2,a3,a4], [b1,b2,b3,b4], [c1,c2,c3,c4] and [d1,d2,d3,d4] 2, d3, d4] are mutually orthogonal. Specifically, [a1, a2, a3, a4] and [b1, b2, b3, b4] are mutually orthogonal, that is, a1′*b1+a2′*b2+a3′*b3+a4′*b4=0; [a1, a2, a3, a4] and [c1, c2, c3, c4] are mutually orthogonal, that is, a1′*c1+a2′*c2+a3′*c3+a4′*c4=0, and so on. No further details are given here.

[0235] In a feasible implementation manner, the value of the second number is 4, the second number of non-zero value symbols constitutes a non-zero value symbol group [p1, p2, p3, p4], and the values ​​of [p1, p2, p3, p4] include at least the various situations as shown in Table 1, wherein different serial numbers in Table 1 correspond to different situations.

[0236] In a feasible implementation manner, the symbol length of each extremely sparse pilot is greater than 24, that is, the total number of non-zero value symbols and zero value symbols of each extremely sparse pilot is greater than 24, which is not specifically limited here.

[0237] A feasible implementation method is that when the value of the first number is greater than or equal to 2, the first number of extremely sparse pilots are independent of each other, that is, the first number of extremely sparse pilots are not associated or related, wherein the value of the first number can be greater than or equal to 1, that is, the value of the first number can be 1, 2 or other values, and no specific limitation is made here. Among them, the technology of including 2 or more pilots in one transmission and the pilots are not associated or independent of each other is called independent multi-pilot technology, and the multiple independent pilots are called independent multi-pilots. Figure 3 As shown, w extremely sparse pilots are included in one transmission, where the w extremely sparse pilots are respectively represented as P1, P2, ..., Pw, w can be a positive integer greater than 2, and the data packet contains information about the w extremely sparse pilots. For example, the data packet contains the index numbers of the w extremely sparse pilots (that is, the index numbers of the extremely sparse pilots in the preset pilot set). In this way, once the data packet of a terminal is successfully decoded, the information of all extremely sparse pilots used by the terminal in this information transmission can be determined, so that interference with the pilot signal can be eliminated.

[0238] It is understandable that the information transmission between the first communication node and the second communication node can adopt independent multi-pilot technology. In this way, under the same pilot overhead, the probability of simultaneous collision of independent multi-pilots of different first communication nodes will be smaller than the probability of collision of traditional single pilots. Therefore, in a transmission scenario of a competitive connectionless state (or a competitive scheduling-free mode), independent multi-pilot technology can be adopted to support more first communication nodes for information transmission. Furthermore, independent multi-pilot technology and extremely sparse pilot technology can be combined, that is, multiple independent and extremely sparse pilots are adopted to further reduce the probability of pilot collision and further increase the number of first communication nodes connected.

[0239] In one embodiment, when the second communication node is a base station, through an iterative receiver, the base station can demodulate the corresponding first communication node in each round through multiple non-colliding (i.e., independent of each other) extremely sparse pilots, and then reconstruct the data packet and extremely sparse pilot of the first communication node, and eliminate the data packet and extremely sparse pilot corresponding to the first communication node from the received signal. This iteration is repeated until all decomposable first communication nodes are demodulated to reduce the probability of pilot collision and further increase the number of accessed first communication nodes.

[0240] In one embodiment, when the value of the first number is greater than or equal to 2, the first number of extremely sparse pilots may be determined according to information in the data packet.

[0241] In another embodiment, when the value of the first number is greater than or equal to 2, the first number of extremely sparse pilots can be determined based on one or more bits of information in the data packet. For example, an extremely sparse pilot can be determined based on one bit of information in the data packet; for another example, an extremely sparse pilot can be determined based on two bits of information in the data packet; for another example, both extremely sparse pilots are determined based on multiple bits of information in the data packet, and so on. The embodiment of the present application does not limit the first number and the number of bit information.

[0242] In another embodiment, when the value of the first number is greater than or equal to 2, each extremely sparse pilot is determined from a preset pilot set based on a fourth number of bits in the data packet, where the preset pilot set includes a fifth number of pilots, and the fourth number and the fifth number form a logarithmic function relationship, where the logarithmic function is a logarithmic function with a base of 2. For example, assuming that the fifth number is D, the fourth number is log2(D), without specific limitation herein. It is understood that the fifth number can be 64, 128, or more, without specific limitation herein.

[0243] In a feasible implementation mode, when the modulation symbols are modulated according to the first constellation model, a1, a2, ..., a N1 can be expressed by the following formula, namely

[0244] a n =(2n-1+Δ)d;

[0245] Among them, the value of n includes 1, 2, ..., N1, that is, a n It can be a1, a2, a2, or a N1 Etc. d is a positive real number, Δ is a real number greater than or equal to 0, such that a1, a2, ..., a N1 Form an arithmetic progression.

[0246] Furthermore, when the value of Δ is 0 and the value of d is 1, so that a n Satisfy a n =2n-1; when Δ is 1 and d is 1 / 2, then a n Satisfy a n =n; when Δ is 3 and d is 1 / 2, then a n Satisfy a n =n+1.

[0247] Alternatively, the value of Δ can be At this time, when the value of d is 1, making a n satisfy When the value of d is 1 / 2, so that a n satisfy

[0248] In a feasible implementation mode, when the modulation symbols are modulated according to the second constellation model, a1, a2, ..., a N2 Both can be expressed by the following formula:

[0249] a n =(2n-1+Δ)d;

[0250] b1,b2,…,b N2 Both can be expressed by the following formula:

[0251] b n =a n +β;

[0252] Among them, the value of n includes 1, 2, ..., N2, that is, a n It can be a1, a2, a3, or a N2 Etc. Similarly, b n It can be b1, b2, b3 or b N2 Etc. d is a positive real number, Δ and β are both real numbers greater than or equal to 0, such that a1, a2,…, a N2 Construct an arithmetic progression, b1, b2,…, b N2 Form an arithmetic progression.

[0253] Furthermore, when the value of Δ is 0 and the value of d is 1, so that a n Satisfy a n =2n-1; when Δ is 1 and d is 1 / 2, then a n Satisfy a n =n; when Δ is 3 and d is 1 / 2, then a n Satisfy a n =n+1.

[0254] Alternatively, the value of Δ can be At this time, when the value of d is 1, making a n satisfy When the value of d is 1 / 2, so that a n satisfy

[0255] In a feasible implementation mode, when the modulation symbols are modulated according to the third constellation model, a1, a2, ..., a N3 Both can be expressed by the following formula:

[0256] a n =(2n-1+Δ)d;

[0257] b1,b2,…,b N3Both can be expressed by the following formula:

[0258] b n =a n +β;

[0259] Among them, the value of n includes 1, 2, ..., N3, that is, a n It can be a1, a2, a3, or a N3 Etc. Similarly, b n It can be b1, b2, b3, or b N3 Etc. d is a positive real number, Δ and β are both real numbers greater than or equal to 0, such that a1, a2,…, a N3 Construct an arithmetic progression, b1, b2,…, b N3 Form an arithmetic progression.

[0260] Furthermore, when the value of Δ is 0 and the value of d is 1, so that a n Satisfy a n =2n-1; when Δ is 1 and d is 1 / 2, then a n Satisfy a n =n; when Δ is 3 and d is 1 / 2, then a n Satisfy a n =n+1.

[0261] Alternatively, the value of Δ can be At this time, when the value of d is 1, making a n satisfy When the value of d is 1 / 2, so that a n satisfy In a feasible implementation manner, when the modulation symbol is modulated according to the second constellation model or the third constellation model, β is equal to 0.

[0262] In a feasible implementation manner, when the modulation symbol is modulated according to the third constellation model, β is greater than 0.

[0263] In a feasible implementation manner, when the modulation symbol is modulated according to the first constellation diagram model, the value of d is a value that makes the average power of the modulation symbol obtained by modulation using the first constellation diagram model equal to 1, that is, the value of d makes the mean of the square of the modulus of the constellation points in the first constellation diagram model is 1, that is, the value of d makes the average power of the first constellation diagram model is 1, and no specific limitation is given here.

[0264] In a feasible implementation manner, when the modulation symbol is modulated according to the second constellation diagram model, the value of d is a value that makes the average power of the modulation symbol obtained by modulation using the second constellation diagram model equal to 1, that is, the value of d makes the mean of the square of the modulus of the constellation points in the second constellation diagram model is 1, that is, the value of d makes the average power of the second constellation diagram model is 1, and no specific limitation is given here.

[0265] In a feasible implementation manner, when the modulation symbol is modulated according to the third constellation model, the value of d is a value that makes the average power of the modulation symbol obtained by modulation using the third constellation model equal to 1, that is, the value of d makes the mean of the square of the modulus of the constellation points in the third constellation model is 1, that is, the value of d makes the average power of the third constellation model is 1, and no specific limitation is given here.

[0266] In a feasible implementation manner, the value of θ may be 0; or, the value of θ may be π / 4, that is, satisfying the formula θ=π / 4; or, the value of θ satisfies the formula θ=π / 8, and no specific limitation is given here.

[0267] like Figure 5 As shown, Figure 5 : is a schematic diagram of a first constellation diagram model and a second constellation diagram model provided in an embodiment of the present application. In one embodiment, the second constellation diagram model can be as follows: Figure 5 The cross-shaped constellation diagram corresponding to the coordinate system in the lower left corner or the cross-shaped constellation diagram corresponding to the coordinate system in the lower right corner, wherein the cross-shaped constellation diagram is a constellation diagram in which half of the constellation points are located on a straight line passing through the zero point (i.e., the origin), and the other half of the constellation points are located on another straight line passing through the zero point (i.e., the origin), and these two straight lines are perpendicular to each other. The cross-shaped constellation diagram has the advantages of high spectral efficiency and simple geometric shape. Specifically, Figure 5 The cross-shaped constellation diagram shown in is a constellation diagram in a two-dimensional signal plane. These cross-shaped constellations include 16 constellation points, each constellation point corresponds to a modulation symbol, and each modulation symbol can carry 4 bits of information, that is, 4 bits of information will be mapped (ie, modulated) into one modulation symbol. Among them, Figure 5 The constellation points in the cross-shaped constellation diagram in the lower left corner are distributed on the x-axis (i.e., I path) and the y-axis (i.e., Q path); Figure 5 The constellation points in the cross-shaped constellation diagram in the lower right corner are distributed on the straight line at 45° and the straight line at 135° passing through the origin. Figure 5 The cross-shaped constellation diagram in the lower right corner can be Figure 5 The cross constellation diagram in the lower left corner is rotated 45 degrees to form the second constellation diagram model. It can be understood that the second constellation diagram model can also be in addition to the following Figure 5For other cross-shaped constellation diagrams other than the cross-shaped constellation diagrams shown in the lower left corner and the lower right corner, the embodiment of the present application does not specifically limit the form of the second constellation diagram model.

[0268] like Figure 5 As shown, in one embodiment, the first constellation model can be as follows Figure 5 The PAM (Pulse Amplitude Modulation) constellation diagram corresponding to the coordinate system in the upper left corner or the PAM constellation diagram corresponding to the coordinate system in the upper right corner is a linear constellation diagram, wherein all constellation points of the PAM constellation diagram are on a straight line passing through the zero point (i.e., the origin). It is understandable that the first constellation diagram model can also be in addition to the following Figure 5 For other PAM constellation diagrams other than the PAM constellation diagrams shown in the upper left corner and the upper right corner, the embodiment of the present application does not specifically limit the form of the first constellation diagram model.

[0269] Specifically, each modulation symbol (i.e., each constellation point) can carry multiple bits of information, enabling high-order modulation and high spectral efficiency. In one embodiment, each modulation symbol can carry four bits of information, meaning that four bits of information are mapped (i.e., modulated) into one modulation symbol. In another embodiment, each modulation symbol can carry five bits, meaning that five bits of information are mapped (i.e., modulated) into one modulation symbol.

[0270] It can be understood that the linear constellation diagram (i.e., PAM constellation diagram), cross constellation diagram and 8-arm constellation diagram corresponding to the modulation symbols all have the advantage of simple geometric shapes. Even if the modulation symbols received by the receiving side (i.e., the second communication node) have undergone channel rotation and scaling, the constellation diagram corresponding to the modulation symbols is only a linear constellation diagram, cross constellation diagram or 8-arm constellation diagram that has been rotated and scaled, and the resulting geometric shape is still relatively simple.

[0271] Since a linear constellation diagram is a relatively simple constellation diagram and is usually easier to process than a cross constellation diagram, the following description will take a slightly more complex cross constellation diagram as an example.

[0272] like Figure 6 As shown, Figure 6 is a schematic diagram of the cross constellation diagram before and after channel rotation and scaling, where Figure 6 The coordinate system on the left is a schematic diagram of the cross constellation diagram corresponding to the transmitted modulation symbol s (i.e., the modulation symbol s at the first communication node that has not been subjected to channel rotation and scaling). Figure 6 The intermediate coordinate system is a schematic diagram of the cross constellation diagram corresponding to the modulation symbol h*s (i.e., h multiplied by s, also expressed as h·s or hs) after rotation and scaling received by the second communication node, where the complex number h is the rotation scaling amount.

[0273] It is worth noting that Figure 6 The intermediate coordinate system is a schematic diagram of a cross constellation diagram corresponding to the received modulation symbol without AWGN (ie, the modulation symbol received by the second communication node after rotation and scaling). Figure 6 The coordinate system on the right is a schematic diagram of the cross-shaped constellation diagram corresponding to the received modulation symbol (y=h*s+n) with AWGN. It can be understood that Figure 6 The constellation diagram shown on the right can be obtained by Figure 6 The constellation points in the constellation diagram shown in the middle are formed by adding the complex numbers corresponding to AWGN, that is, the constellation points corresponding to the received modulation symbols (h*s+n) with AWGN will be Figure 6 The constellation point (h*s) corresponding to the constellation diagram shown in the middle is distributed around the constellation point according to the probability density of AWGN. Figure 6 In the constellation diagram on the right, the colors of the constellation points change from dark to light from the center to the edge. The constellation points are the set of points formed by the corresponding modulation symbols affected by AWGN. Figure 6 The constellation diagram on the right also shows that even with AWGN, the general shape of the cross constellation diagram corresponding to the received modulation symbol is still a cross. Therefore, the receiving side (i.e., the second communication node) can use the following Figure 6 The geometric shape of the cross constellation diagram shown on the right is used to estimate the rotation and scaling of the constellation diagram, that is, to estimate h.

[0274] The following is a detailed description of a rotation scaling estimation method:

[0275] like Figure 7 As shown, first, the two-dimensional plane (i.e., the two-dimensional signal plane) is divided into four partitions, and two typical methods can be used for partitioning. Specifically, Figure 7 As shown in the coordinate system on the left, in the first partitioning method, the four quadrants are divided into four partitions, that is, the x-axis and y-axis are the partition lines. Among them, the area filled with oblique lines is partition 1, the area filled with fine dots is partition 2, the area filled with vertical lines is partition 3, and the area filled with bricks is partition 4; Figure 7As shown in the coordinate system on the right, the four partitions in the second partitioning method are formed by rotating the four partitions in the first partitioning method by 45°, that is, the area enclosed by the 45° ray emitted from the origin to the 135° ray emitted from the origin is partition 1, where partition 1 is filled with oblique lines; the area enclosed by the 135° ray emitted from the origin to the 225° ray emitted from the origin is partition 2, where partition 2 is filled with fine dots; the area enclosed by the 225° ray emitted from the origin to the 315° ray emitted from the origin is partition 3, where partition 3 is filled with vertical lines; the area enclosed by the 315° ray emitted from the origin to the 45° ray emitted from the origin is partition 4, where partition 4 is filled with bricks. Figure 7 The two partitioning methods shown determine the partition to which a constellation point belongs. Simply performing some simple addition and subtraction on the constellation point coordinates is sufficient to determine the specific partition to which the constellation point belongs, without requiring complex multiplication operations. This demonstrates the simplicity of the determination method. In addition to the two partitioning methods described above, other partitioning methods can be used to divide the two-dimensional plane into four partitions, which are not specifically limited in this embodiment of the present application.

[0276] like Figures 6 to 8 As shown, after the receiving side (i.e., the second communication node) divides the two-dimensional signal plane into four partitions, the constellation points in each partition (i.e., the modulation symbols corresponding to each constellation point) are added up, and then divided by the number of constellation points in the partition (i.e., the number of modulation symbols). Then, a coordinate can be calculated, which is the center of the constellation point of the partition. Figure 6 The cross-shaped constellation diagram shown in the middle is Figure 6 The cross-shaped constellation diagram shown on the left is a schematic diagram of the constellation diagram formed after rotation and scaling. Figure 7 Taking the partition shown in the coordinate system on the left as an example, after partitioning, all constellation points are divided into 4 parts, such as Figure 8 As shown in the middle coordinate system and the right coordinate system, the constellation point center c1 of partition 1 can be obtained by adding up the constellation points in partition 1 and dividing it by the number of constellation points in the partition. Figure 8 The position of the triangle shown in the coordinate system on the right; similarly, by adding up the constellation points in partition 2 and dividing it by the number of constellation points in the partition, we can get the constellation point center c2 of partition 2, that is, Figure 8 The position of the quadrilateral shown in the coordinate system on the right; add up the constellation points in partition 3 and divide it by the number of constellation points in the partition to get the constellation point center c3 of partition 3, that is Figure 8 The position of the five-pointed star shown in the coordinate system on the right; add up the constellation points in partition 4 and divide it by the number of constellation points in the partition to get the constellation point center c4 of partition 4, that is Figure 8 The position of the hexagonal star is shown in the coordinate system on the right.

[0277] like Figure 7 and Figure 8 As shown in the figure, the rotation and scaling of the entire constellation diagram can be obtained according to the constellation point centers of all partitions. Specifically, Figure 8 Taking a partitioning method shown as an example, assuming that the calculated constellation point centers of the four partitions are c1, c2, c3, and c4 respectively, c2′ is obtained by rotating the constellation point center c2 of partition 2 clockwise by 90°, that is, c2′=c2*(-j); c3′ is obtained by rotating the constellation point center c3 of partition 3 clockwise by 180°, that is, c3′=-c3; c4′ is obtained by rotating the constellation point center c4 of partition 4 counterclockwise by 90°, that is, c4′=c4*j; then, based on c1, c2′, c3′, and c4′, the rotation scaling amount c of the entire constellation diagram can be estimated, wherein the rotation scaling amount c can be expressed by the following formula (1), that is:

[0278] c=(c1+c2′+c3′+c4′) / 4 (1)

[0279] In the presence of AWGN, especially when some modulation symbols are subject to large AWGN, some modulation symbols may be handed over. In order to more accurately estimate the rotation and scaling amount, it is usually necessary to use Figure 7 For the two partitioning methods shown in , two rotation scaling values ​​of the constellation diagram are calculated according to the above estimation method for the two partitioning methods respectively, and then the larger modulus of the two rotation scaling values ​​is used as the rotation scaling value of the constellation diagram.

[0280] like Figure 5 As shown, for Figure 5 For the linear constellation diagram shown in the upper left or upper right corner, only two partitions can be used to calculate the rotation scaling of the constellation diagram. For example, after the receiving side (i.e., the second communication node) divides the two-dimensional signal plane into two partitions through the y-axis, the constellation points in each partition (i.e., the modulation symbols corresponding to each constellation point) are added up, and then divided by the number of constellation points in the partition (i.e., the number of modulation symbols). Then, a constellation point can be calculated, i.e., the constellation point center of the partition. Then, the rotation scaling of the entire constellation diagram is obtained by using the constellation point centers of all partitions. Assume that the right side of the x-axis (i.e., x>=0) is partition 1, and the constellation point center of partition 1 is c1; the left side of the x-axis (i.e., x<0) is partition 2, and the constellation point center of partition 2 is c2. By rotating the constellation point center c2 of partition 2 clockwise by 90°, c2′ is obtained, i.e., c2′=-c2; then, the rotation scaling c of the entire constellation diagram can be estimated based on c1 and c2′, wherein the rotation scaling c can be expressed by the following formula (2):

[0281] c=(c1+c2′) / 2 (2)

[0282] In order to more accurately estimate the rotation scaling amount, the following four different 2-partitioning methods can be used for partitioning. In the first partitioning method, the x-axis is used as the partition line to divide the two-dimensional signal plane into two partitions; in the second method, the y-axis is used as the partition line to divide the two-dimensional signal plane into two partitions; in the third partitioning method, the 45° straight line passing through the origin is used as the partition line to divide the two-dimensional signal plane into two partitions; in the fourth partitioning method, the 135° straight line passing through the origin is used as the partition line to divide the two-dimensional signal plane into two partitions.

[0283] Based on the above four different 2-partition methods, four rotation scaling amounts are calculated, and then the one with the largest modulus among the four rotation scaling amounts is used as the rotation scaling amount of the constellation diagram. After the receiving side (i.e., the second communication node) estimates the rotation scaling amount of the constellation diagram, the rotation scaling amount experienced by the constellation diagram can be balanced to obtain a constellation diagram without distortion and only affected by AWGN.

[0284] Therefore, the multiple modulation symbols obtained through the first constellation model, the second constellation model or the third constellation model can form a constellation with a simple geometric shape, and after the modulation symbols are distorted by rotation and scaling due to channel interference, the formed constellation still presents a simple geometric shape. Therefore, the information transmission method of the present application can compensate only through the shape characteristics of the constellation, thereby eliminating the need to increase pilot overhead to improve demodulation performance and ensure high-frequency spectrum efficiency.

[0285] The information transmission method provided in the above embodiment is described in detail below using specific examples:

[0286] Example 1:

[0287] Reference Figure 6 , Figure 6 The cross-shaped constellation diagram in can be divided into two parts, and the constellation points of each part are on a straight line passing through the zero point (i.e. the origin). For example, Figure 6 In the cross-shaped constellation diagram corresponding to the coordinate system on the left, half of the constellation points fall on the straight line of the x-axis, and the other half fall on the straight line of the y-axis. Figure 6 Half of the constellation points in the cross-shaped constellation diagram corresponding to the intermediate coordinate system fall on a straight line passing through the zero point (i.e., the origin) at an angle of 45° to the positive semi-axis of the x-axis, and the other half of the constellation points fall on a straight line passing through the zero point (i.e., the origin) at an angle of 135° to the positive semi-axis of the x-axis.

[0288] Specifically, if the distances between adjacent constellation points on a straight line passing through the origin are equal, and the distance between two adjacent points is set to 2d, then among the four constellation points closest to the origin, the distances between adjacent constellation points are only That is to say, among the four constellation points closest to the origin, the distance between adjacent constellation points will be smaller than the distance between adjacent constellation points on the same straight line, that is, the four constellation points closest to the origin are more densely distributed. Therefore, the constellation diagram is more susceptible to AWGN interference, which will lead to a decrease in demodulation performance.

[0289] In addition, the cross-shaped constellation diagram can be divided into 4 parts, for example, Figure 6 The cross-shaped constellation diagram corresponding to the coordinate system on the left can be obtained according to Figure 7 The partitioning form shown in the coordinate system on the right will be as follows Figure 6 The constellation points in the cross-shaped constellation diagram corresponding to the left coordinate system are divided into 4 parts, among which the constellation points in the first part are the constellation points greater than 0 on the x-axis, that is, the constellation points falling on the positive half axis of the x-axis. Figure 7 Partition 4 of the coordinate system on the right; the constellation points in the second part are the constellation points on the x-axis that are less than 0, that is, the constellation points that fall on the negative half axis of the x-axis, where the second part corresponds to Figure 7 Partition 2 of the coordinate system on the right; the constellation points in the third part are the constellation points on the y-axis that are greater than 0, that is, the constellation points that fall on the positive half axis of the y-axis, where the third part corresponds to Figure 7 Partition 1 of the coordinate system on the right; the constellation points in the fourth part are the constellation points on the y-axis that are less than 0, that is, the constellation points that fall on the negative half axis of the y-axis, where the fourth part corresponds to Figure 7 Partition 3 of the coordinate system on the right.

[0290] Furthermore, in order to avoid the above problem (i.e., among the four constellation points closest to the origin, the distance between adjacent constellation points will be smaller than the distance between adjacent constellation points on the same straight line), an offset Δ greater than 0 can be added to the constellation points of the four parts of the cross-shaped constellation diagram, so that among the four constellation points closest to the origin, the distance between adjacent constellation points is greater than or equal to the distance between adjacent constellation points on the same straight line. That is, the constellation points of the four parts are all offset in a direction away from the origin, thereby avoiding a dense distribution of the four constellation points closest to the origin, thereby improving demodulation performance.

[0291] Alternatively, the constellation points of the four parts of the cross-shaped constellation diagram may not be superimposed with an offset Δ greater than 0, that is, the offset of the constellation points of each part of the cross-shaped constellation diagram is 0. In a cross-shaped constellation diagram in which the offsets of the constellation points of all parts are 0, the distances between adjacent constellation points on the same straight line are equal, and therefore, the average power of the constellation diagram is lower. Specifically, in a n=(2n-1+Δ)d, the value of Δ can be at this time, Among the four constellation points closest to the origin, the distance between adjacent constellation points is 2d, and the distance between adjacent constellation points on the same straight line is also 2d. That is, among the four constellation points closest to the origin, the distance between adjacent constellation points is equal to the distance between adjacent constellation points on the same straight line in each part.

[0292] It is understandable that in order to improve the transmission performance of the four constellation points closest to the origin in the cross constellation diagram, the distance between adjacent constellation points in the four constellation points closest to the origin can be increased, so that the formed cross constellation diagram expands outward, avoiding the four constellation points closest to the origin from being too densely distributed, thereby reducing the impact of AWGN on the constellation points (i.e., modulation symbols) and improving the robustness of the cross constellation diagram. For example, it can be set a n =nd, d is a positive real number, so that among the four constellation points closest to the origin, the distance between adjacent constellation points is The distance between adjacent constellation points on the same straight line in each portion is d, that is, among the four constellation points closest to the origin, the distance between adjacent constellation points is greater than the distance between adjacent constellation points on the same straight line in each portion, that is, the constellation points of the four portions are offset in a direction away from the origin to reduce the impact of AWGN on the constellation points (i.e., modulation symbols), thereby improving the demodulation performance of the second communication node. However, since adding an offset Δ greater than 0 to the constellation points of the four portions of the cross constellation diagram will increase the average power of the constellation diagram, some scenarios may also use a cross constellation diagram with an offset Δ of 0, which is not specifically limited here.

[0293] Example 2:

[0294] The value of Δ satisfies the formula For example, refer to Figure 9 When the second constellation model is a cross constellation, when the value of M2 is 1, the 3 bits of information in the data packet can be modulated using the second constellation model to obtain a modulation symbol. Since N2 = 2 M2 , corresponding to N2=2, therefore, the second constellation model is a cross constellation including 8 constellation points, where the value of d is 1, i.e., the scaling amount of the cross constellation is 1; the value of θ is 0, i.e., the rotation amount of the cross constellation is 0, that is, the constellation points in the cross constellation are distributed on the x-axis (i.e., I path) and the y-axis (i.e., Q path). Next, by It can be seen that Therefore, constellation point a1e j0 (ie s1) and constellation point b1ej(0+π / 2) The distance between them (i.e. s3) is 2, i.e. Among them, e j0 =cos 0+jsin0=1,e j(0+π / 2) = cos(0+π / 2)+jsin(0+π / 2)=j, so it can be determined that the distance between adjacent constellation points on the same straight line is 2. Similarly, constellation point a1e j0 (ie s1) and constellation point a2e j0 The distance between them (i.e. s2) is 2, i.e. The distance between the adjacent points of the 4 constellation points closest to the origin is 2. Therefore, the distance between constellation points s1 and s3 is equal to the distance between constellation points s1 and s2. Therefore, the distance between the adjacent points of the 4 constellation points closest to the origin is equal to the distance between adjacent constellation points on the same straight line. Among them, the coordinates of constellation point s1 are The coordinates of constellation point s2 are The coordinates of constellation point s3 are It is understandable that the two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the second constellation diagram model, which will not be described in detail here.

[0295] From this we can see that when Δ is equal to In the case of Figure 9 The two-dimensional coordinates of the eight constellation points shown are as follows:

[0296]

[0297]

[0298]

[0299]

[0300] In addition, the two-dimensional coordinates of the eight constellation points may include the following:

[0301] (1+Δ,0),(3+Δ,0),

[0302] (0,1+Δ),(0,3+Δ),

[0303] (-(1+Δ),0),(-(3+Δ),0),

[0304] (0,-(1+Δ)),(0,-(3+Δ))

[0305] Among them, Δ can be expressed as a finite decimal, for example, No specific limitation is imposed here.

[0306] When power normalization needs to be performed on the second constellation model, the two-dimensional coordinates of the eight constellation points corresponding to the second constellation model may be uniformly multiplied by a normalization factor.

[0307] Example 3:

[0308] The value of Δ satisfies the formula For example, refer to Figure 10 When the second constellation model is a cross constellation, when the value of M2 is 1, the 3 bits of information in the data packet can be modulated using the second constellation model to obtain a modulation symbol. Since N2 = 2 M2 , corresponding to N2=2, therefore, the second constellation diagram model is a cross constellation diagram including 8 constellation points, wherein the value of d is 1, that is, the scaling amount of the cross constellation diagram is 1; the value of θ is π / 4, that is, the rotation amount of the cross constellation diagram is π / 4, that is, half of the constellation points in the cross constellation diagram fall on a straight line passing through the zero point (i.e., the origin) at an angle of 45° to the positive semi-axis of the x-axis, and the other half of the constellation points fall on a straight line passing through the zero point (i.e., the origin) at an angle of 135° to the positive semi-axis of the x-axis.

[0309] Then, by It can be seen that

[0310] It is understandable that the two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the second constellation diagram model, which will not be described in detail here.

[0311] From this we can see that when Δ is equal to In the case of Figure 10 The two-dimensional coordinates of the eight constellation points shown are as follows:

[0312]

[0313]

[0314]

[0315] It is understandable that the value of Δ can also satisfy the formula Here, Δ can be expressed by a finite decimal, for example, Δ=1-0.707=0.293, which is not specifically limited here.

[0316] When the value of Δ satisfies the formula The two-dimensional coordinates of the eight constellation points may include the following:

[0317]

[0318]

[0319]

[0320]

[0321] When power normalization needs to be performed on the second constellation model, the two-dimensional coordinates of the eight constellation points corresponding to the second constellation model may be uniformly multiplied by a normalization factor.

[0322] Example 4:

[0323] Reference Figure 11 When the second constellation model is a cross constellation, when M2 is 2, the 4 bits of information in the data packet can be modulated using the second constellation model to obtain a modulation symbol. Since N2 = 2 M2 , corresponding to N2=4, therefore, the second constellation model is a cross constellation with 16 constellation points, where the value of d is 1, i.e., the scaling amount of the cross constellation is 1; the value of θ is 0, i.e., the rotation amount of the cross constellation is 0, that is, the constellation points in the cross constellation are distributed on the x-axis (i.e., I path) and the y-axis (i.e., Q path). Next, by It can be seen that Due to e j0 =cos 0+jsin0=1, so Thus, a1e can be determined j0 with a2e j0 The distance between adjacent constellation points on the same straight line is 2. In addition, according to b n =a n +β, when β is 0, we can get b n =a n , that is, b n with a n Equal, because e j(0+π / 2) =cos(0+π / 2)+jsin(0+v / 2)=j, therefore, Thus, a1e can be determined j0 with b1e j(0+π / 2) The distance between the adjacent points of the 4 constellation points closest to the origin is 2. Therefore, the distance between the adjacent points of the 4 constellation points closest to the origin is equal to the distance between adjacent constellation points on the same straight line. Referring to the calculation method in the above example 3, the coordinates of constellation point s1 can be determined to be The coordinates of constellation point s2 are The two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the second constellation diagram model, which will not be described in detail here.

[0324] From this we can see that when Δ is equal to In the case of Figure 11 The two-dimensional coordinates of the 16 constellation points shown are as follows:

[0325]

[0326]

[0327]

[0328]

[0329] In addition, the two-dimensional coordinates of the 16 constellation points may include the following:

[0330] (1+Δ,0),(3+Δ,0),(5+Δ,0),(7+Δ,0),

[0331] (-(1+Δ),0),(-(3+Δ),0),(-(5+Δ),0),(-(7+Δ),0),

[0332] (0,1+Δ),(0,3+Δ),(0,5+Δ),(0,7+Δ),

[0333] (0,-(1+Δ)),(0,-(3+Δ)),(0,-(5+Δ)),(0,-(7+Δ))

[0334] Among them, Δ can be expressed as a finite decimal, for example, No specific limitation is imposed here.

[0335] When power normalization needs to be performed on the second constellation model, the two-dimensional coordinates of the 16 constellation points corresponding to the second constellation model may be uniformly multiplied by a normalization factor.

[0336] Example 5:

[0337] Reference Figure 12 When the second constellation model is a cross constellation, when the value of M2 is 2, the 4 bits of information in the data packet can be modulated using the second constellation model to obtain a modulation symbol. Since N2 = 2 M2, corresponding to N2=4, therefore, the second constellation model is a cross constellation with 16 constellation points, wherein the value of d is 1, that is, the scaling amount of the cross constellation is 1; the value of θ is π / 4, that is, the rotation amount of the cross constellation is π / 4, that is, half of the constellation points in the cross constellation fall on a straight line passing through the zero point (i.e., the origin) at an angle of 45° to the positive half axis of the x-axis, and the other half of the constellation points fall on a straight line passing through the zero point (i.e., the origin) at an angle of 135° to the positive half axis of the x-axis. Next, by a n =(2n-1+Δ)d, we can see that a n =2n-1+Δ, if That is to say From this we get therefore So with a1e jπ / The coordinates of the corresponding constellation point s1 are (1,1), which is the same as a2e jπ / The coordinates of the corresponding constellation point s2 are It is understandable that the two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the second constellation diagram model, which will not be described in detail here.

[0338] From this we can see that when Δ is equal to In the case of Figure 12 The two-dimensional coordinates of the 16 constellation points shown are as follows:

[0339]

[0340]

[0341]

[0342]

[0343] It is understandable that the value of Δ can also satisfy the formula Here, Δ can be expressed by a finite decimal, for example, Δ=1-0.707=0.293, which is not specifically limited here.

[0344] When the value of Δ satisfies the formula The two-dimensional coordinates of the 16 constellation points may include the following:

[0345]

[0346]

[0347]

[0348]

[0349]

[0350]

[0351]

[0352]

[0353] because Thus, a1e can be determined jπ / with a2e jπ / The distance between adjacent constellation points on the same straight line is 2. In addition, due to therefore, Thus, a1e can be determined j π / with a1e j(π / 4+π / 2) The distance between the adjacent points of the 4 constellation points closest to the origin is 2. Therefore, the distance between the adjacent points of the 4 constellation points closest to the origin is equal to the distance between adjacent constellation points on the same straight line.

[0354] When power normalization needs to be performed on the second constellation model, the two-dimensional coordinates of the 16 constellation points corresponding to the second constellation model may be uniformly multiplied by a normalization factor.

[0355] Example 6:

[0356] Take the value of Δ satisfying the formula Δ=0 as an example, refer to Figure 13 When the second constellation model is a cross constellation, when the value of M2 is 1, the 3 bits of information in the data packet can be modulated using the second constellation model to obtain a modulation symbol. Since N2 = 2 M2 , corresponding to N2=2, therefore, the second constellation model is a cross constellation including 8 constellation points, where the value of d is 1, i.e., the scaling amount of the cross constellation is 1; the value of θ is 0, i.e., the rotation amount of the cross constellation is 0, that is, the constellation points in the cross constellation are distributed on the x-axis (i.e., I path) and the y-axis (i.e., Q path). Next, by a n =(2n-1+Δ)d, we can see that a n =2n-1, so we can determine a1=1, a2=3. j0 = cos 0 + jsin0 = 1, so a1e j0 =1,a2e j0 =3, so a1e j0The coordinates of the corresponding constellation point s1 are (1,0), a2e j0 The coordinates of the corresponding constellation point s2 are (3, 0). It is understandable that the two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the second constellation diagram model, which will not be repeated here.

[0357] From this we can see that when Δ is equal to 0, that is, Figure 13 The two-dimensional coordinates of the eight constellation points shown are as follows:

[0358] (1,0),(3,0),

[0359] (0,1),(0,3),

[0360] (-1,0),(-3,0),

[0361] (0,-1),(0,-3)

[0362] When it is necessary to perform power normalization on the second constellation model, the two-dimensional coordinates of the eight constellation points corresponding to the second constellation model may be uniformly multiplied by a normalization factor (such as 1 / sqrt(10)).

[0363] Example 7:

[0364] Take the value of Δ satisfying the formula Δ=0 as an example, refer to Figure 14 When the second constellation model is a cross constellation, when the value of M2 is 1, the 3 bits of information in the data packet can be modulated using the second constellation model to obtain a modulation symbol. Since N2 = 2 M2 , corresponding to N2=2, therefore, the second constellation diagram model is a cross constellation diagram including 8 constellation points, wherein the value of d is 1, that is, the scaling amount of the cross constellation diagram is 1; the value of θ is π / 4, that is, the rotation amount of the cross constellation diagram is π / 4, that is, half of the constellation points in the cross constellation diagram fall on a straight line passing through the zero point (i.e., the origin) at an angle of 45° to the positive semi-axis of the x-axis, and the other half of the constellation points fall on a straight line passing through the zero point (i.e., the origin) at an angle of 135° to the positive semi-axis of the x-axis. Then, by a n =(2n-1+Δ)d, we can see that a n =2n-1, from which we can get a1=1, a2=3, then Therefore, with a1e jπ / 4 The coordinates of the corresponding constellation point s1 are with a2e jπ / 4 The coordinates of the corresponding constellation point s2 are It is understandable that the two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the second constellation diagram model, which will not be described in detail here.

[0365] It can be seen that the two-dimensional coordinates of the eight constellation points may include the following:

[0366]

[0367]

[0368]

[0369]

[0370] When it is necessary to perform power normalization on the second constellation model, the two-dimensional coordinates of the eight constellation points corresponding to the second constellation model may be uniformly multiplied by a normalization factor (such as 1 / sqrt(10)).

[0371] Example 8:

[0372] Reference Figure 15 When the second constellation model is a cross constellation, when the value of M2 is 2, the 4 bits of information in the data packet can be modulated using the second constellation model to obtain a modulation symbol. Since N2 = 2 M2 , corresponding to N2=4, therefore, the second constellation diagram model is a cross constellation diagram including 16 constellation points, wherein the value of d is 1, that is, the scaling amount of the cross constellation diagram is 1; the value of θ is 0, that is, the rotation amount of the cross constellation diagram is 0, that is, the constellation points in the cross constellation diagram are distributed on the x-axis (i.e., I-path) and the y-axis (i.e., Q-path).

[0373] Then, by a n =(2n-1+Δ)d, so a n =2n-1+Δ, if Δ=0, that is, a n =2n-1, so a1=1, a2=3. j0 =cos0+jsin0=1, so a1e can be determined j0 =e j0 =1,a2e j0 =3e j0 =3, so with a1e j0 The coordinates of the corresponding constellation point s1 are (1,0), which is the same as a2e j0 The coordinates of the corresponding constellation point s2 are (3, 0). It is understandable that the two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the second constellation diagram model, which will not be repeated here.

[0374] It can be seen that the two-dimensional coordinates of the 16 constellation points may include the following:

[0375] (1,0),(3,0),(5,0),(7,0),

[0376] (-1,0),(-3,0),(-5,0),(-7,0),

[0377] (0,1),(0,3),(0,5),(0,7),

[0378] (0,-1),(0,-3),(0,-5),(0,-7)

[0379] When it is necessary to perform power normalization on the second constellation model, the two-dimensional coordinates of the 16 constellation points corresponding to the second constellation model may be uniformly multiplied by a normalization factor (eg, 1 / sqrt(84)).

[0380] Example 9:

[0381] Reference Figure 16 When the second constellation model is a cross constellation, when the value of M2 is 2, the 4 bits of information in the data packet can be modulated using the second constellation model to obtain a modulation symbol. Since N2 = 2 M2 , corresponding to N2=4, therefore, the second constellation model is a cross constellation with 16 constellation points, wherein the value of d is 1, that is, the scaling amount of the cross constellation is 1; the value of θ is π / 4, that is, the rotation amount of the cross constellation is π / 4, that is, half of the constellation points in the cross constellation fall on a straight line passing through the zero point (i.e., the origin) at an angle of 45° to the positive half axis of the x-axis, and the other half of the constellation points fall on a straight line passing through the zero point (i.e., the origin) at an angle of 135° to the positive half axis of the x-axis. Next, by a n =(2n-1+Δ)d, so a n =2n-1+Δ, if Δ=0, that is, a n =2n-1. From this we get a1=1, a2=3. Then Therefore, with a1e jπ / 4 The coordinates of the corresponding constellation point s1 are with a2e jπ / 4 The coordinates of the corresponding constellation point s2 are It is understandable that the two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the second constellation diagram model, which will not be described in detail here.

[0382] Therefore, the two-dimensional coordinates of the 16 constellation points may include the following:

[0383]

[0384]

[0385]

[0386]

[0387] When it is necessary to perform power normalization on the second constellation model, the two-dimensional coordinates of the 16 constellation points corresponding to the second constellation model may be uniformly multiplied by a normalization factor (eg, 1 / sqrt(84)).

[0388] Example 10:

[0389] Take the value of Δ satisfying the formula Δ=0 as an example, refer to Figure 17 When the second constellation model is a cross constellation, when the value of M2 is 1, the 3 bits of information in the data packet can be modulated using the second constellation model to obtain a modulation symbol. Since N2 = 2 M2 , corresponding to N2=2, therefore, the second constellation model is a cross constellation including 8 constellation points, where the value of d is 1, i.e., the scaling amount of the cross constellation is 1; the value of θ is 0, i.e., the rotation amount of the cross constellation is 0, that is, the constellation points in the cross constellation are distributed on the x-axis (i.e., I path) and the y-axis (i.e., Q path). Next, by a n =2n-1, we know that a1=1, a2=2, since e j0 =cos 0+jsin0=1, so we can determine a1e j0 =1,a2e j0 =2, so a1e j0 The coordinates of the corresponding constellation point s1 are (1,0), a2e j0 The coordinates of the corresponding constellation point s2 are (2, 0). It is understandable that the two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the second constellation diagram model, which will not be repeated here.

[0390] It can be seen that the two-dimensional coordinates of the eight constellation points may include the following:

[0391] (1,0),(2,0),

[0392] (0,1),(0,2),

[0393] (-1,0),(-2,0),

[0394] (0,-1),(0,-2)

[0395] When power normalization is required for the second constellation model, the two-dimensional coordinates of the eight constellation points corresponding to the second constellation model may be uniformly multiplied by a normalization factor (eg, 1 / sqrt(5)).

[0396] Example 11:

[0397] Take the value of Δ satisfying the formula Δ=0 as an example, refer to Figure 18 When the second constellation model is a cross constellation, when the value of M2 is 1, the 3 bits of information in the data packet can be modulated using the second constellation model to obtain a modulation symbol. Since N2 = 2 M2 , corresponding to N2=2, therefore, the second constellation diagram model is a cross constellation diagram including 8 constellation points, wherein the value of d is 1, that is, the scaling amount of the cross constellation diagram is 1; the value of θ is π / 4, that is, the rotation amount of the cross constellation diagram is π / 4, that is, half of the constellation points in the cross constellation diagram fall on a straight line passing through the zero point (i.e., the origin) at an angle of 45° to the positive semi-axis of the x-axis, and the other half of the constellation points fall on a straight line passing through the zero point (i.e., the origin) at an angle of 135° to the positive semi-axis of the x-axis. Then, by a n =2n-1, we know that a1=1, a2=2, then Therefore, with a1e jπ / 4 The coordinates of the corresponding constellation point s1 are with a2e jπ / 4 The coordinates of the corresponding constellation point s2 are It is understandable that the two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the second constellation diagram model, which will not be described in detail here.

[0398] It can be seen from this that the complex numbers corresponding to the 8 constellation points in the second constellation diagram model can be expressed as follows:

[0399]

[0400]

[0401]

[0402]

[0403] Therefore, the second constellation model can be as follows Figure 18 The cross-shaped constellation diagram shown includes 8 constellation points. That is, the constellation diagram corresponding to θ taking a value of π / 4 can be obtained by rotating the constellation diagram corresponding to θ taking a value of 0 by 45°. The two-dimensional coordinates of the 8 constellation points may include the following:

[0404]

[0405]

[0406]

[0407]

[0408] Example 12:

[0409] Reference Figure 19 When the first constellation model is a PAM constellation model, and the value of M1 is 2, the first constellation model can be used to modulate the 3 bits of information in the data packet to obtain a modulation symbol. Since N=2 M , corresponding to N1=4, therefore, the first constellation model is a PAM constellation diagram including 8 constellation points, where the value of d is 1, that is, the scaling amount of the PAM constellation diagram is 1; the value of θ is 0, that is, the rotation amount of the PAM constellation diagram is 0, that is, the constellation points in the PAM constellation diagram are distributed on the x-axis (i.e., I-path). Next, by a n =(2n-1+Δ)d, we can see that if Δ=0, that is, a n =2n-1. From this we get a1=1, a2=3. Then a1e j0 =e j0 =1,a2e j0 =3e j0 =3, so with a1e j0 The coordinates of the corresponding constellation point s1 are (1,0), which is the same as a2e j0 The coordinates of the corresponding constellation point s2 are (3, 0). It is understandable that the two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the first constellation diagram model, which will not be repeated here.

[0410] It can be seen that the two-dimensional coordinates of the eight constellation points may include the following:

[0411] (1,0),(3,0),(5,0),(7,0),

[0412] (-1,0),(-3,0),(-5,0),(-7,0)

[0413] When it is necessary to perform power normalization on the first constellation model, the two-dimensional coordinates of the eight constellation points corresponding to the first constellation model may be uniformly multiplied by a normalization factor (eg, 1 / sqrt(84)).

[0414] Example 13:

[0415] Take the value of Δ satisfying the formula Δ=0 as an example, refer to Figure 20When the first constellation model is a PAM constellation model, when the value of M1 is 1, the first constellation model can be used to modulate the 2 bits of information in the data packet to obtain a modulation symbol. Since N1 = 2 M1 , corresponding to N1=2, therefore, the first constellation model is a PAM constellation diagram including 4 constellation points, where the value of d is 1, that is, the scaling amount of the PAM constellation diagram is 1; the value of θ is 0, that is, the rotation amount of the PAM constellation diagram is 0, that is, the constellation points in the PAM constellation diagram are distributed on the x-axis (i.e., I-axis). Then, by a n =2n-1, we know that a2=2. Then a1e j0 =e j0 =1,a2e j0 =2e j0 =2, so, with a1e j0 The coordinates of the corresponding constellation point s1 are (1,0), which is the same as a2e j0 The coordinates of the corresponding constellation point s2 are (2, 0). It is understandable that the two-dimensional coordinates of other constellation points can be calculated using the complex forms corresponding to the constellation points in the first constellation diagram model, which will not be repeated here.

[0416] Therefore, the two-dimensional coordinates of the four constellation points may include the following:

[0417] (1,0),(2,0),

[0418] (-1,0),(-2,0)

[0419] When power normalization is required for the first constellation model, the two-dimensional coordinates of the four constellation points corresponding to the first constellation model may be uniformly multiplied by a normalization factor (eg, 1 / sqrt(5)).

[0420] It is understandable that the coordinates corresponding to each constellation point in the second constellation diagram model may include the following:

[0421] (a1cosθ,a1sinθ),(a2cosθ,a2sinθ),…,(a n cosθ,a n sinθ),

[0422]

[0423] (a1cos(θ+π),a1sin(θ+π)),(a2cos(θ+π),a2sin(θ+π)),…,(a n cos(θ+π),a n sin(θ+π)),

[0424] (a1cos(θ+3π / 2),a1sin(θ+3π / 2)),(a2cos(θ+3π / 2),a2sin(θ+3π / 2)),…,(a n cos(θ+3π / 2),a n sin(θ+3π / 2))

[0425] According to the trigonometric formula, the coordinates corresponding to each constellation point in the second constellation diagram model can also be expressed as follows:

[0426] (a1cosθ,a1sinθ),(a2cosθ,a2sinθ),…,(a n cosθ,a n sinθ)

[0427] (-a1sinθ,a1cosθ),(-a2sinθ,a2cosθ),…,(-a n sinθ,a n cosθ)

[0428] (-a1cosθ,-a1sinθ),(-a2cosθ,-a2sinθ),…,(-a n cosθ,-a n sinθ)

[0429] (a1sinθ,-a1cosθ),(a2sinθ,-a2cosθ),…,(a n sinθ,-a n cosθ)

[0430] Among them, the trigonometric function formulas include the following:

[0431] cos(θ+π / 2)=-sinθ

[0432] sin(θ+π / 2)=cosθ

[0433] cos(θ+π)=-cosθ

[0434] sin(θ+π)=-sinθ

[0435] cos(θ+3π / 2)=sinθ

[0436] sin(θ+3π / 2)=-cosθ

[0437] It is worth noting that when the value of θ is 0, that is, the rotation amount of the cross constellation diagram is 0, the constellation points in the cross constellation diagram are distributed on the x-axis and the y-axis. Therefore, the coordinates corresponding to each constellation point in the second constellation diagram model may include the following:

[0438] (a1,0),(a2,0),…,(a n ,0),

[0439] (0,a1),(0,a2),…,(0,a n ),

[0440] (-a1,0),(-a2,0),…,(-a n ,0),

[0441] (0,-a1),(0,-a2),…,(0,-a n )

[0442] It is worth noting that when θ is π / 4, that is, the rotation amount of the cross constellation diagram is π / 4, the constellation points in the cross constellation diagram are respectively distributed on a straight line in a 45° direction passing through the origin and a straight line in a 135° direction passing through the origin. Therefore, the coordinates corresponding to each constellation point in the second constellation diagram model may include the following:

[0443]

[0444]

[0445]

[0446]

[0447] Example 14:

[0448] Reference Figure 21 , Figure 21 is a schematic diagram of the third constellation diagram model provided in an embodiment of the present application, wherein the third constellation diagram model can be understood as an 8-arm constellation diagram. Figure 21 The constellation points in the 8-arm constellation diagram corresponding to the coordinate system on the left are respectively distributed on the straight line passing through the x-axis (i.e., I path) (including the ray of the positive half axis and the ray of the negative half axis), the straight line passing through the y-axis (i.e., Q path) (including the ray of the positive half axis and the ray of the negative half axis), the ray passing through the origin in the 45° direction, the ray passing through the origin in the 135° direction, the ray passing through the origin in the 225° direction, and the ray passing through the origin in the 315° direction. For the third constellation diagram model, when b n =a n , can be formed as Figure 21 The 8-arm constellation diagram corresponding to the intermediate coordinate system, when b n =a n +β, can form Figure 21 The 8-arm constellation diagram corresponding to the coordinate system on the right.

[0449] It is understandable that Figure 21 The 8-arm constellation diagram corresponding to the coordinate system on the right can be obtained by Figure 21 The amplitudes of the constellation points of four arms (the rays in the 45°, 135°, 225°, and 315° directions passing through the origin) in the 8-arm constellation corresponding to the intermediate coordinate system are expanded outward as a whole, which can make the constellation points of the star constellation more evenly distributed, thereby improving the demodulation performance.

[0450] Example 15:

[0451] Reference Figure 22 , Figure 22 Schematic diagram of the third constellation model provided in the embodiment of the present application, wherein the third constellation model can be understood as an 8-arm constellation. When M3=0, the modulation symbol is obtained by modulating the 3 bits of information in the data packet according to the third constellation model, and N3=2 M3 , corresponding to N3 = 1, therefore, the third constellation model is an 8-arm constellation including 8 constellation points. Figure 22 The constellation points in the 8-arm constellation diagram corresponding to the coordinate system on the left are respectively distributed on the straight line passing through the x-axis (i.e., I path) (including the ray of the positive half axis and the ray of the negative half axis), the straight line passing through the y-axis (i.e., Q path) (including the ray of the positive half axis and the ray of the negative half axis), the ray passing through the origin in the 45° direction, the ray passing through the origin in the 135° direction, the ray passing through the origin in the 225° direction, and the ray passing through the origin in the 315° direction. For the third constellation diagram model, when b n =a n , can be formed as Figure 22 The 8-arm constellation diagram corresponding to the coordinate system on the left, when b n =a n +β, can form Figure 22 The 8-arm constellation diagram corresponding to the middle or right coordinate system.

[0452] It is understandable that Figure 22 The 8-arm constellation diagram corresponding to the coordinate system on the right can be obtained by Figure 22 The amplitudes of the constellation points of four arms (the rays passing through the origin in the directions of 45°, 135°, 225°, and 315°) in the eight-arm constellation diagram corresponding to the coordinate system on the left are expanded outward as a whole, which can make the constellation points of the star-shaped constellation diagram more evenly distributed, thereby improving the demodulation performance.

[0453] The information transmission method provided in the above embodiment is exemplified below by taking extremely sparse pilots as an example.

[0454] In one embodiment, a demodulation reference signal (DMRS) set may be defined, wherein the set includes 12 reference signals. Demodulation reference signals may also be referred to as demodulation reference signal ports (DMRS ports). In other words, a set including 12 demodulation reference signal ports (DMRS ports) may be defined.

[0455] In one embodiment, if Figure 23 As shown, Figure 23 A schematic diagram of defining a physical resource block is provided in an embodiment. Figure 23 In the , a physical resource block (PRB) can be defined, which contains 14 orthogonal frequency division multiplexing (or Discrete Fourier Transform-Spread-Orthogonal Frequency Division Multiplexing, DFT-S-OFDM) or Single-carrier Frequency-Division Multiple Access, SC-FDMA) symbols in the time domain and 12 subcarriers in the frequency domain. Each small grid represents a subcarrier of an OFDM symbol, also commonly known as a resource element (RE), so the physical resource block (PRB) contains a total of 12×14=168 resource elements (RE). Since the first two OFDM symbols are used to carry the demodulation reference signal, that is, the first two OFDM symbols are used as the reference signal (DMRS) area, the resource overhead occupied by the demodulation reference signal (DMRS) is 1 / 7. Among them, the area except the reference signal (DMRS) area is the modulation symbol area.

[0456] In one embodiment, if Figure 24 As shown, Figure 24 A schematic diagram of defining a demodulation reference signal is provided for one embodiment. 12 demodulation reference signals (DMRS) can be divided into three groups based on the position of the occupied resource unit (RE). The non-zero value symbols (or non-zero signals, useful signals, etc.) of the first group of demodulation reference signals (DMRS) (i.e., the symbols are non-zero values) are carried on the first resource unit (RE), and the four DMRS ports can be distinguished by the OCC code; the non-zero value symbols of the second group of demodulation reference signals (DMRS) are carried on the second resource unit (RE), and the four DMRS ports can be distinguished by the OCC code; the non-zero value symbols of the third group of demodulation reference signals (DMRS) are carried on the third resource unit (RE), and the four DMRS ports can be distinguished by the OCC code. Among them, in Figure 24In the diagram, the small square where the first resource unit is located is filled with vertical lines, the small square where the second resource unit is located is filled with horizontal lines, and the small square where the third resource unit is located is filled with wavy lines. Each set of demodulation reference signals takes the value of 0 (i.e., no signal) on the resource units (REs) in the blank, unfilled pattern. It can be seen that for each set of demodulation reference signals, not all resource units (REs) in the reference signal area have signals. However, for a first communication node (such as a terminal), even if the reference signal port it uses has no signal only on some REs in the reference signal area, it still cannot use the REs without signals to transmit information. Therefore, the resource overhead occupied by the reference signal (or reference signal port) in each set of demodulation reference signals is also 1 / 7.

[0457] If the non-zero value symbols of each group of demodulation reference signals are carried on the same resource element (RE), different reference signals can only be distinguished by the non-zero value symbols with different values, for example, different reference signal ports can be distinguished by the time domain OCC code and the frequency domain OCC code. Figure 25 As shown, Figure 25 A schematic diagram of distinguishing different reference signal ports by using OCC codes is provided in an embodiment. Figure 24 Taking the first group of four demodulation reference signals in as an example, the four demodulation reference signal ports, i.e., the group of DMRS ports, can be separated by jointly using two long OCC codes [1,1] and [1,-1] in the time domain and two long OCC codes [1,1] and [1,-1] in the frequency domain. Different DMRS ports are generated by carrying different OCC codes on the first resource unit. Figure 24 The situation of the four reference signals in the second group and the four reference signals in the third group is similar. Therefore, a total of 12 demodulation reference signals of the defined demodulation reference signal (DMRS) set, that is, 12 demodulation reference signal ports, can be obtained.

[0458] In one embodiment, if Figure 26 As shown, Figure 26 A schematic diagram of an embodiment of a method for defining a demodulation reference signal using an OCC code is provided. Figure 24 The four demodulation reference signals in the first group can be separated by jointly using two long OCC codes [1,1], [1,-1] in the time domain and two long OCC codes [1,1], [1,-1] in the frequency domain, wherein Figure 26 In the figure, the numbers in the shaded parts of the first to third columns are all 1 from top to bottom, the numbers in the shaded parts of the fourth column are all -1 from top to bottom, the numbers in the shaded parts of the fifth to seventh columns are 1, -1, 1, -1 from top to bottom, and the numbers in the shaded parts of the eighth column are -1, 1, -1, 1 from top to bottom.

[0459] In one embodiment, if Figure 27 As shown, Figure 27 FIG1 is another schematic diagram of defining a demodulation reference signal using an OCC code according to an embodiment. Figure 24 The four demodulation reference signals in the second group can be separated by jointly using two long OCC codes [1,1], [1,-1] in the time domain and two long OCC codes [1,1], [1,-1] in the frequency domain, wherein Figure 27 In the figure, the numbers in the shaded parts of the first to third columns are all 1 from top to bottom, the numbers in the shaded parts of the fourth column are all -1 from top to bottom, the numbers in the shaded parts of the fifth to seventh columns are 1, -1, 1, -1 from top to bottom, and the numbers in the shaded parts of the eighth column are -1, 1, -1, 1 from top to bottom.

[0460] In one embodiment, if Figure 28 As shown, Figure 28 Schematic diagram of another demodulation reference signal using an OCC code provided by an embodiment. 8 represents the first reference signal unit, 9 represents the second reference signal unit; Figure 24 The four demodulation reference signals in the third group can be separated by jointly using two long OCC codes [1,1] and [1,-1] in the time domain and two long OCC codes [1,1] and [1,-1] in the frequency domain. Figure 28 In the figure, the numbers in the shaded parts of the first to third columns are all 1 from top to bottom, the numbers in the shaded parts of the fourth column are all -1 from top to bottom, the numbers in the shaded parts of the fifth to seventh columns are 1, -1, 1, -1 from top to bottom, and the numbers in the shaded parts of the eighth column are -1, 1, -1, 1 from top to bottom.

[0461] In this application, the reference signals carried by several resource elements (REs) adjacent in the time domain and frequency domain may be referred to as a reference signal element (RSE). Figures 23 to 28 In the IEEE Spectrum Distributed Access (SDA) framework, a reference signal carried by four consecutive resource elements (REs) in the time and frequency domain is called a reference signal element (RSE). Figuratively, the reference signal on a grid filled with a pattern is an RSE. From a channel estimation perspective, in addition to being composed of adjacent resource elements in the time or frequency domain, an RSE also has another characteristic: when using the reference signal for channel estimation, each RSE can estimate a channel value.

[0462] According to this definition, Figures 23 to 28As shown in the figure, in the defined demodulation reference signal (DMRS) set, each reference signal has two reference signal elements (RSEs) within one PRB bandwidth. Therefore, a channel value at point 2 within one PRB bandwidth (that is, within the bandwidth of 12 subcarriers) can be estimated. In addition, the channel values ​​of the 12 subcarriers within one PRB bandwidth can be interpolated from these reference signal element estimates.

[0463] In one embodiment, if Figure 29 As shown, Figure 29 A schematic diagram of a PRB-based transmission provided in one embodiment. If a transmission contains X PRBs, the 12 demodulation reference signals (or 12 demodulation reference signal ports) in the reference signal set are as follows: Figure 29 As shown, each reference signal has 2×X reference signal elements (RSEs), so the channel values ​​at 2×X equally spaced locations within the entire transmission bandwidth can be estimated, and then the channel values ​​of all 12×X subcarriers within the transmission bandwidth can be obtained by interpolation.

[0464] Based on the above embodiment, the 12 demodulation reference signals (DMRS) can be divided into three groups based on the location of the occupied resource elements (REs). Figure 30 A schematic diagram of another method for defining a demodulation reference signal is provided in an embodiment. Figure 30 , the first group of 4 demodulation reference signals can be distinguished by OCC codes; Figure 31 A schematic diagram of another method for defining a demodulation reference signal is provided in an embodiment. Figure 31 , a second group of four demodulation reference signals that can be distinguished by OCC codes; Figure 32 Another implementation diagram of defining a demodulation reference signal is provided in an embodiment. Figure 32 In the example, the third group of 4 demodulation reference signals can be distinguished by OCC codes.

[0465] It can be seen that in order to estimate the channel of the entire transmission bandwidth of each accessed terminal, the demodulation reference signal (or pilot) occupies a large amount of resources. In other words, the distribution of the demodulation reference signal in the entire transmission bandwidth has a certain density and cannot be too sparse. Figures 20 to 32 In the illustrated embodiment, the density of demodulation reference signals in the entire transmission bandwidth is 2 reference signals per PRB, or 2 reference signal elements (RSEs) per PRB.

[0466] For the system, the reference signal overhead is 1 / 7. This means that the system expends 1 / 7 of the resources to design only 12 demodulation reference signals. For information transmission in a connectionless transmission state, the probability of collision between any two reference signals independently selected by terminals is 1 / 12, which is very high. Therefore, demodulation reference signals severely limit the number of terminals that can transmit information in a connectionless state. For information transmission in SPS scenarios, 12 demodulation reference signals can only support 12 terminals. Therefore, demodulation reference signals severely limit the number of terminals that can transmit information in SPS scenarios.

[0467] If the reference signal also needs to estimate a certain frequency offset, the resources occupied by each reference signal will continue to increase. In other words, the density of each reference signal in the transmitted signal will continue to increase. For example, if the reference signal is repeated once in the time domain to estimate the frequency offset, the resources occupied by the reference signal will double, that is, the resource overhead will be 2 / 7. In other words, to estimate the frequency-selective channel and frequency offset, the system will spend 2 / 7 of the resources and can only design 12 demodulation reference signals. If the system further needs to cope with a certain timing offset, the resources occupied by the reference signal will continue to increase. For example, the system will spend 3 / 7 or even 4 / 7 of the overhead to design 12 demodulation reference signals. Such a large overhead can only obtain a small number of reference signals (i.e., reference signal ports). Therefore, the collision probability of reference signals transmitted in the disconnected state is very high, and the number of terminals transmitting information in the SPS scenario will also be limited.

[0468] If the multipath channel changes more rapidly in the frequency domain, meaning its frequency-selective nature becomes more pronounced, the density of demodulation reference signals in the frequency domain will increase further to ensure accurate channel estimation. Each set of demodulation reference signals has three reference signal units within each PRB bandwidth (visually, three grids). Therefore, three estimated values ​​can be obtained for each PRB, and 3×X estimated values ​​can be obtained for X PRBs. Linear interpolation can then be used to determine the channel for all subcarriers in the X PRBs. This reference signal also accounts for 1 / 7 of the transmission resource overhead, but only eight demodulation reference signals (eight demodulation reference signal ports) can be allocated, which is less than the number of demodulation reference signals defined above. Therefore, channel estimation capability is generally inversely proportional to the number of reference signals.

[0469] Therefore, the problem faced by reference signals applied to connectionless transmission scenarios and SPS-based information transmission scenarios is that the reference signals must not only estimate the frequency-selective channel and time-frequency offset of the entire transmission channel, but also identify the terminal device. Therefore, the time-frequency resources occupied by the reference signals increase exponentially, which leads to a serious shortage of reference signals under certain resources, and in turn affects the number of terminals that can transmit information in connectionless transmission scenarios and SPS-based information transmission scenarios.

[0470] The main starting point of this application is to greatly reduce the task of reference signals, thereby minimizing the resources occupied by each reference signal, that is, making the density of each reference signal in the transmission signal as sparse as possible, and then maximizing the number of reference signals, and ultimately increasing the number of terminals performing information transmission in connectionless transmission scenarios and SPS-based information transmission scenarios.

[0471] Specifically, the present application uses data-based channel estimation technology (rather than reference signal-based) to estimate the channel of the entire transmission bandwidth and the time-frequency offset through the characteristics of the data itself, such as the geometric characteristics of the constellation diagram of the modulation symbol. In other words, there is no need to use a reference signal to estimate the channel and time-frequency offset of the entire transmission bandwidth. Taking channel estimation as an example, in order to simplify the description, taking the block flat fading channel as an example, the four partitioning methods in the above embodiment can be used to estimate the rotation and scaling of the constellation diagram, that is, the block flat fading channel can be estimated by the four partitioning methods in the above embodiment, which will not be described in detail here.

[0472] Therefore, in the embodiment of the present application, the task of the reference signal is much smaller than that of the related scheme, so the resources occupied by each reference signal in the embodiment of the present application are less than the resources occupied by each reference signal in the related scheme. Therefore, under a certain overhead, the number of reference signals in the present application is more than the number of reference signals in the related scheme.

[0473] On the other hand, when a base station has multiple receiving antennas, for example, R receiving antennas, theoretically, these R receiving antennas can provide very strong spatial capabilities, thereby improving the performance of multi-terminal access. In order to obtain this spatial capability, this application proposes to use "extremely sparse" reference signals to estimate the spatial channel h experienced by each terminal signal. k =[h k1 ,h k2 ,...,h kR ] t , where t is the transposition operator, and then the spatial channel is used to obtain the spatial merging weight, and then the received signals of the R receiving antennas are spatially merged. Specifically, the signal of terminal k is spatially merged to obtain the modulation symbol s k =h k'*y, where y=[y k1 ,y k2 ,...,y kR ] t is the received signal of R receiving antennas, h k ′ is h k The conjugate transpose of the modulated symbol s is then used by the receiver to combine the modulated symbols s in the spatial domain. k Estimate the channel of the entire transmission bandwidth experienced by the signal of terminal k and estimate the time-frequency offset, and then calculate the modulation symbol s after spatial domain combination k Compensate for the channel and time-frequency offset, and finally demodulate and decode the modulation symbols that compensate for the channel and time-frequency offset.

[0474] Therefore, the present application does not use the reference signal to estimate the channel within the entire transmission bandwidth, nor does it use it to estimate the time-frequency offset.

[0475] In one embodiment, Figure 33 This is a schematic diagram of defining a reference signal. Assuming the reference signal occupies one OFDM symbol, a single transmission consists of X PRBs of time-frequency resources. A physical resource block (PRB) contains 14 OFDM (or DFT-S-OFDM or SC-FDMA) symbols in the time domain and 12 subcarriers in the frequency domain. The first OFDM symbol is used to carry the demodulation reference signal, meaning the first OFDM symbol serves as the extremely sparse pilot region. Thus, 1 / 14 of the resources are used to transmit the reference signal, meaning 12 x X resource elements (REs) are used to transmit the reference signal. The area outside the extremely sparse pilot region is the modulation symbol region.

[0476] In one embodiment, if Figure 34 As shown, Figure 34 This diagram shows a reference signal (i.e., an extremely sparse pilot) defined for another system. Each reference signal has a non-zero symbol (non-zero signal, or useful signal) on only one RE resource element, and no signal (i.e., the value is 0) on the remaining resource elements. Therefore, it can occupy 1 / 14 of the reference signal area with an overhead, and a total of 12×X reference signals can be allocated. Specifically, if there are 6 PRBs and the resource overhead of each PRB is 1 / 14, 6×12=72 reference signals can be allocated, which is much larger than the number of reference signals in the NR system (the number of reference signals in the NR system is 8 or 12, and the resource overhead occupied by the reference signals in the NR system is still 1 / 7).

[0477] In one embodiment, if Figure 35 As shown, Figure 35This is a schematic diagram of another definition of reference signals (i.e., extremely sparse pilot ports). Each reference signal defined by the system has non-zero value symbols (or non-zero signals, or useful signals) only on 2 RE resource units. Every 2 REs can be separated into 2 reference signals through a 2-length OCC. There is no signal on the remaining resource units (i.e., the value is 0). Therefore, it can occupy a reference signal area of ​​1 / 14 overhead, and a total of 12×X reference signals can be separated. Specifically, if there are 6 PRBs and the resource overhead of each PRB is 1 / 14 overhead, 6×12=72 reference signals can be separated, and the number of reference signals is much larger than the number of reference signals in the NR system (the number of reference signals in the NR system is 8 or 12). Therefore, the number of non-zero value symbols of the extremely sparse pilot is proportional to the number of PRBs.

[0478] In one embodiment, if Figure 36 As shown, Figure 36 A schematic diagram of generating a DMRS port is provided in an embodiment, wherein different OCC codes (such as OCC code 1 and OCC code 2) are carried on two REs to generate different DMRS ports, wherein Figure 36 In the diagram, RE is represented by two small squares filled with vertical lines.

[0479] In one embodiment, if Figure 37 As shown, Figure 37 A schematic diagram of another method for defining a reference signal provided by an embodiment, wherein the reference signal defined in the system occupies 2 OFDM symbols.

[0480] In one embodiment, if Figure 38 As shown, Figure 38 This is a schematic diagram of another definition of reference signals provided by an embodiment. Each reference signal defined by the system has a non-zero value symbol (or non-zero signal, or useful signal) only on a group of 4 adjacent RE resource units, but there will be 4 reference signals multiplexing a group of 4 adjacent REs, where the 4 reference signals multiplexing the same group of 4 adjacent REs can be distinguished by the OCC code. Therefore, when a transmission includes X PRBs and each PRB occupies 1 / 7 of the reference signal area of ​​the overhead, a total of 24×X reference signals can be separated. Specifically, if a transmission includes 6 PRBs and each PRB occupies 1 / 7 of the resource overhead, 6×24=144 reference signals can be separated. Therefore, the number of reference signals is much larger than the number of reference signals in the NR system (the number of reference signals in the NR system is 8 or 12). At the same time, it illustrates that the number of extremely sparse pilots is proportional to the number of PRBs.

[0481] It is worth noting that the numerical values ​​shown in all the above embodiments are only exemplary descriptions and are not specifically limited. The numerical values ​​can be adaptively adjusted according to actual conditions.

[0482] As can be seen, extremely sparse pilots are pilots with very few non-zero elements (i.e., non-zero-valued symbols) in the preset pilot set, for example, only 1-4 non-zero elements. Therefore, the extremely sparse pilot solution can significantly increase the number of pilots without increasing pilot overhead, thereby significantly reducing the probability of pilot collisions. Furthermore, the base station can estimate partial information about the wireless channel from the extremely sparse pilots, rather than the entire channel. Furthermore, the base station can further extract channel information from the modulation symbols and use this channel information to perform modulation symbol equalization.

[0483] It should be noted that the extremely sparse pilot is only used for spatial merging but cannot be used for channel equalization. Therefore, the extremely sparse pilot can be considered as a spatial merging reference signal and is not specifically limited here.

[0484] It should also be noted that although Figure 33 、 Figure 34 、 Figure 35 and Figure 36 The extremely sparse reference signals (i.e., extremely sparse pilots) shown in the figure are all located at the first symbol, or the first symbol and the second symbol of the transmission resource, but the present application does not limit the position of the extremely sparse reference signal. For example, the position of the extremely sparse reference signal can also be located in the middle of the transmission resource.

[0485] It can be understood that the information transmission in all the above embodiments is information in a broad sense, that is, the information can be business data or information used for system control, that is, signaling; or, the information can include bit data that needs to be transmitted, such as business bit data or signaling bit data, where different English expressions such as message, information, payload, etc. can all represent information.

[0486] It can be understood that the first communication node in all the above embodiments can be a terminal, for example, a mobile phone, a smart phone, a laptop computer, a PDA (Personal Digital Assistant), a PAD (tablet computer), a navigation device and other mobile terminals, or an Internet of Things device terminal, etc., without specific limitation here.

[0487] It can be understood that the second communication node in all the above embodiments can be a base station, a receiver, an access point, etc., and no specific limitation is made here.

[0488] In addition, refer to Figure 39An embodiment of the present application further provides a communication device 100, which includes at least one processor 101 and at least one memory 102, and the memory 102 is used to store at least one program.

[0489] The processor 101 and the memory 102 may be connected via a bus or other means.

[0490] The memory 102 is a non-transitory computer-readable storage medium that can be used to store non-transitory software programs and non-transitory computer executable programs. In addition, the memory 102 may include a high-speed random access memory and may also include a non-transitory memory, such as at least one disk storage device, a flash memory device, or other non-transitory solid-state storage device. In some embodiments, the memory 102 may optionally include a memory remotely located relative to the processor 101, and these remote memories may be connected to the processor 101 via a network. Examples of the above-mentioned network include, but are not limited to, the Internet, an intranet, a local area network, a mobile communication network, and combinations thereof.

[0491] The non-transient software program and instructions required to implement the information transmission method of the above embodiment are stored in the memory 102. When executed by the processor 101, the information transmission method of the above embodiment is executed, for example, the above-described Figure 2 Method steps S110 to S120 and Figure 4 Method step S210 in .

[0492] The device embodiments described above are merely illustrative. The units described as separate components may or may not be physically separate, i.e., they may be located in one place or distributed across multiple network units. Some or all of the modules may be selected based on actual needs to achieve the objectives of this embodiment.

[0493] In addition, an embodiment of the present application further provides a computer-readable storage medium, which stores computer-executable instructions. The computer-executable instructions are executed by a processor or controller, for example, by a processor in the above-mentioned device embodiment, so that the above-mentioned processor can execute the information transmission method in the above-mentioned embodiment and execute the above-mentioned Figure 2 Method steps S110 to S120 and Figure 4 Method step S210 in .

[0494] In addition, one embodiment of the present application further provides a computer program product, including a computer program or computer instructions, wherein the computer program or computer instructions are stored in a computer-readable storage medium, and a processor of a computer device reads the computer program or computer instructions from the computer-readable storage medium, and the processor executes the computer program or computer instructions, so that the computer device executes the information transmission method in the above embodiment, for example, executing the above-described Figure 2 Method steps S110 to S120 and Figure 4 Method step S210 in .

[0495] Those skilled in the art will appreciate that all or some of the steps and systems in the method disclosed above can be implemented as software, firmware, hardware, and appropriate combinations thereof. Some physical components or all physical components can be implemented as software executed by a processor, such as a central processing unit, a digital signal processor, or a microprocessor, or implemented as hardware, or implemented as an integrated circuit, such as an application-specific integrated circuit. Such software can be distributed on a computer-readable medium, and the computer-readable medium can include computer storage media (or non-transitory media) and communication media (or temporary media). As known to those skilled in the art, the term computer storage media is included in any method or technology for storing information (such as computer-readable instructions, data structures, program modules, or other data) and is volatile and non-volatile, removable, and non-removable. Computer storage media includes, but is not limited to, RAM, ROM, EEPROM, flash memory, or other memory technology, CD-ROM, digital versatile disks (DVD), or other optical disk storage, magnetic cassettes, magnetic tapes, disk storage, or other magnetic storage devices, or any other medium that can be used to store desired information and can be accessed by a computer. Furthermore, as is well known to those skilled in the art, communication media typically embodies computer-readable instructions, data structures, program modules, or other data in a modulated data signal such as a carrier wave or other transport mechanism, and may include any information delivery media.

Claims

1. An information transmission method, applied to a first communication node, comprising: determining a first number of very sparse pilots; transmitting a data packet together with the first number of the very sparse pilots to a second communication node; Wherein, the first number is greater than or equal to 1, and the data packet contains at least a modulation symbol; The modulation symbol is obtained by modulating M1+1 bits of information in the data packet according to a first constellation model, wherein the first constellation model includes 2*N1 constellation points, M1 is an integer greater than or equal to 1, and N1 and M1 satisfy the formula N1=2 M1 ; The complex forms corresponding to the 2*N1 constellation points in the first constellation diagram model include the following: a1e jθ ,a2e jθ ,…,fence N1 by jθ , a1e j(θ+π) ,a2e j(θ+π) ,…,fence N1 by j(θ+π) 4 π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N1 are all positive numbers and satisfy: 0<a1<a2<…<a N1 ; or, The modulation symbol is obtained by modulating M2+2 bits of information in the data packet according to a second constellation model, wherein the second constellation model includes 4*N2 constellation points, M2 is an integer greater than or equal to 1, and N2 and M2 satisfy the formula N2=2 M2 ; The complex forms corresponding to the 4*N2 constellation points in the second constellation diagram model include the following: a1e jθ ,a2e jθ ,…,fence N2 by jθ , b1e j(θ+π / 2) ,b2e j(θ+π / 2) ,…,b N2 e j(θ+π / 2) , a1e j(θ+π) ,a2e j(θ+π) ,…,fence N2 by j(θ+π) , b1e j(θ+3π / 2) ,b2e j(θ+3π / 2) ,…,b N2 e j(θ+3π / 2) ; π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N2 and b1, b2, …, b N2 are all positive numbers and satisfy: 0<a1<a2<…<a N2 , 0<b1<b2<…<b N2 ; or, The modulation symbol is obtained by modulating M3+3 bits of information in the data packet according to a third constellation model, wherein the third constellation model includes 8*N3 constellation points, M3 is an integer greater than or equal to 0, and N3 and M3 satisfy the formula N3=2 M3 ; The complex forms corresponding to the 8*N3 constellation points in the third constellation diagram model include the following: a1e jθ ,a2e jθ ,…,fence N3 by jθ , a1e j(θ+π) ,a2e j(θ+π) ,…,fence N3 by j(θ+π) , π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N3 and b1, b2, …, b N3 are all positive numbers and satisfy: 0<a1<a2<…<a N3 , 0<b1<b2<…<b N3 .

2. The method according to claim 1, wherein: When the modulation symbol is modulated according to the first constellation model, a1, a2, ..., a N1 Both can be expressed by the following formula: a n =(2n-1+Δ)d; Wherein, the value of n includes 1, 2, ..., N1; d is a positive real number, and Δ is a real number greater than or equal to 0; Alternatively, when the modulation symbol is modulated according to the second constellation model, a1, a2, ..., a N2 Both can be expressed by the following formula: a n =(2n-1+Δ)d; b1, b2, …, b N2 Both can be expressed by the following formula: b n =a n +b; Wherein, the value of n includes 1, 2, ..., N2; d is a positive real number, and Δ and β are both real numbers greater than or equal to 0; Alternatively, when the modulation symbol is modulated according to the third constellation model, a1, a2, ..., a N3 Both can be expressed by the following formula: a n =(2n-1+Δ)d; b1, b2, …, b N3 Both can be expressed by the following formula: b n =a n +b; Wherein, the value of n includes 1, 2, ..., N3; d is a positive real number, and Δ and β are both real numbers greater than or equal to 0.

3. The method according to claim 2, characterized in that The value of Δ is 0, and the value of d is 1, so that a n Satisfy a n =2n-1.

4. The method according to claim 2, characterized in that The value of Δ is 1, and the value of d is 1 / 2, so that a n Satisfy a n =n.

5. The method according to claim 2, characterized in that The value of Δ is 3, and the value of d is 1 / 2, so that a n Satisfy a n =n+1.

6. The method according to claim 2, characterized in that The value of Δ is 7. The method according to claim 6, characterized in that: The value of d is 1, so that a n satisfy Or, d takes the value of 1 / 2, so that a n satisfy 8. The method according to claim 2, characterized in that When the modulation symbol is modulated according to the second constellation model or the third constellation model, β is equal to 0.

9. The method according to claim 2, characterized in that When the modulation symbol is modulated according to the third constellation model, β is greater than 0.

10. The method according to claim 2, wherein: When the modulation symbol is modulated according to the first constellation model, the value of d is a value that makes the average power of the modulation symbol modulated by the first constellation model equal to 1; or, When the modulation symbol is modulated according to the second constellation model, the value of d is a value that makes the average power of the modulation symbol modulated by the second constellation model equal to 1; or, When the modulation symbol is modulated according to the third constellation model, the value of d is a value that makes the average power of the modulation symbol modulated by the third constellation model equal to 1.

11. The method according to claim 1, wherein: The value of θ is 0; or, The value of θ satisfies the formula θ=π / 4; or, The value of θ satisfies the formula θ=π / 8.

12. The method according to claim 1, characterized in that Each of the extremely sparse pilots includes a second number of non-zero value symbols, where the second number is greater than 0 and less than 5, and the second number of non-zero value symbols are carried on a third number of adjacent resource units in the time-frequency domain, or on a third number of symbols in chronological order, or on a third number of resource units on adjacent subcarriers in the frequency domain, wherein the third number is equal to the second number.

13. The method according to claim 1 or 12, characterized in that The symbol length of each of the extremely sparse pilots is greater than 24.

14. The method according to claim 12, wherein: The value of the second number is 1; or, The second number has a value of 2, and the second number of non-zero-valued symbols constitute a non-zero-valued symbol pair [p1, p2], and the value of [p1, p2] is [a1, a2] or [b1, b2], wherein [a1, a2] and [b1, b2] are orthogonal; or, The value of the second number is 2, and the second number of non-zero valued symbols constitutes a non-zero valued symbol pair [p1, p2], and the values ​​of [p1, p2] include at least the following situations: [p1, p2] = [1, 1]; [p1, p2] = [1, -1]; [p1, p2] = [1, j]; [p1, p2] = [1, -j]; or, The second number has a value of 4, and the second number of non-zero-valued symbols constitute a non-zero-valued symbol group [p1, p2, p3, p4], and the value of [p1, p2, p3, p4] is [a1, a2, a3, a4], [b1, b2, b3, b4], [c1, c2, c3, c4] or [d1, d2, d3, d4], wherein [a1, a2, a3, a4], [b1, b2, b3, b4], [c1, c2, c3, c4] and [d1, d2, d3, d4] are mutually orthogonal; or, The value of the second number is 4, and the second number of non-zero-valued symbols constitute a non-zero-valued symbol group [p1, p2, p3, p4], and the values ​​of [p1, p2, p3, p4] include at least the following cases: [p1, p2, p3, p4] = [1, 1, 1, 1]; [p1, p2, p3, p4] = [1, 1, -1, -1]; [p1, p2, p3, p4] = [1, -1, 1, -1]; [p1, p2, p3, p4] = [1, -1, -1, 1]; [p1, p2, p3, p4] = [1, 1, j, -j]; [p1, p2, p3, p4] = [1, 1, -j, j]; [p1, p2, p3, p4] = [1, -1, j, j]; [p1, p2, p3, p4] = [1, -1, -j, -j]; [p1, p2, p3, p4] = [1, j, 1, -j]; [p1, p2, p3, p4] = [1, j, -1, j]; [p1, p2, p3, p4] = [1, -j, 1, j]; [p1, p2, p3, p4] = [1, -j, -1, -j]; [p1, p2, p3, p4] = [1, j, j, -1]; [p1, p2, p3, p4] = [1, j, -j, 1]; [p1, p2, p3, p4] = [1, -j, j, 1]; [p1, p2, p3, p4] = [1, -j, -j, -1]; [p1, p2, p3, p4] = [1, 1, 1, -1]; [p1, p2, p3, p4] = [1, 1, -1, 1]; [p1, p2, p3, p4] = [1, -1, 1, 1]; [p1, p2, p3, p4] = [1, -1, -1, -1]; [p1,p2,p3,p4]=[1,1,j,j]; [p1,p2,p3,p4]=[1,1,-j,-j]; [p1,p2,p3,p4]=[1,-1,j,-j]; [p1,p2,p3,p4]=[1,-1,-j,j]; [p1,p2,p3,p4]=[1,j,1,j]; [p1,p2,p3,p4]=[1,j,-1,-j]; [p1,p2,p3,p4]=[1,-j,1,-j]; [p1,p2,p3,p4]=[1,-j,-1,j]; [p1,p2,p3,p4]=[1,j,j,1]; [p1,p2,p3,p4]=[1,j,-j,-1]; [p1,p2,p3,p4]=[1,-j,j,-1]; [p1,p2,p3,p4]=[1,-j,-j,1]; [p1,p2,p3,p4]=[1,1,1,j]; [p1,p2,p3,p4]=[1,1,-1,-j]; [p1,p2,p3,p4]=[1,-1,1,-j]; [p1,p2,p3,p4]=[1,-1,-1,j]; [p1,p2,p3,p4]=[1,1,j,1]; [p1,p2,p3,p4]=[1,1,-j,-1]; [p1,p2,p3,p4]=[1,-1,j,-1]; [p1,p2,p3,p4]=[1,-1,-j,1]; [p1,p2,p3,p4]=[1,j,1,1]; [p1,p2,p3,p4]=[1,j,-1,-1]; [p1,p2,p3,p4]=[1,-j,1,-1]; [p1,p2,p3,p4]=[1,-j,-1,1]; [p1,p2,p3,p4]=[1,j,j,-j]; [p1,p2,p3,p4]=[1,j,-j,j]; [p1,p2,p3,p4]=[1,-j,j,j]; [p1,p2,p3,p4]=[1,-j,-j,-j]; [p1,p2,p3,p4]=[1,1,1,-j]; [p1,p2,p3,p4]=[1,1,-1,j]; [p1,p2,p3,p4]=[1,-1,1,j]; [p1,p2,p3,p4]=[1,-1,-1,-j]; [p1,p2,p3,p4]=[1,1,j,-1]; [p1,p2,p3,p4]=[1,1,-j,1]; [p1,p2,p3,p4]=[1,-1,j,1]; [p1,p2,p3,p4]=[1,-1,-j,-j]; [p1,p2,p3,p4]=[1,j,1,-1]; [p1,p2,p3,p4]=[1,j,-1,1]; [p1,p2,p3,p4]=[1,-j,1,1]; [p1, p2, p3, p4] = [1, -j, -1, -1]; [p1, p2, p3, p4] = [1, j, j, j]; [p1, p2, p3, p4] = [1, j, -j, -j]; [p1, p2, p3, p4] = [1, -j, j, -j]; [p1, p2, p3, p4] = [1, -j, -j, j].

15. The method according to claim 1, wherein When the value of the first number is greater than or equal to 2: The first number of extremely sparse pilots are independent of each other; or, The first number of the extremely sparse pilots is determined according to information in the data packet; or, The first number of the extremely sparse pilots is determined according to one or more bits of information in the data packet; or, Each of the extremely sparse pilots is determined from a preset pilot set based on a fourth number of bit information in the data packet, wherein the preset pilot set includes a fifth number of pilots, the fourth number is in a logarithmic function relationship with the fifth number, and the logarithmic function is a logarithmic function with base 2.

16. The method according to claim 1, wherein The value of the first number is 1 or 2.

17. An information transmission method, applied to a second communication node, the information transmission method comprising: receiving a data packet and a first number of extremely sparse pilots sent by a first communication node; Wherein, the first number is greater than or equal to 1, and the data packet contains at least a modulation symbol; The modulation symbol is obtained by modulating M1+1 bits of information in the data packet according to a first constellation model, wherein the first constellation model includes 2*N1 constellation points, M1 is an integer greater than or equal to 1, and N1 and M1 satisfy the formula N1=2 M1 ; The complex forms corresponding to the 2*N1 constellation points in the first constellation diagram model include the following: a1e jθ ,a2e jθ ,…,fence N1 by jθ , a1e j(θ+π) ,a2e j(θ+π) ,…,fence N1 by j(θ+π) 4 π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N1 are all positive numbers and satisfy: 0<a1<a2<…<a N1 ; or, The modulation symbol is obtained by modulating M2+2 bits of information in the data packet according to a second constellation model, wherein the second constellation model includes 4*N2 constellation points, M2 is an integer greater than or equal to 1, and N2 and M2 satisfy the formula N2=2 M2 ; The complex forms corresponding to the 4*N2 constellation points in the second constellation diagram model include the following: a1e jθ ,a2e jθ ,…,fence N2 by jθ , b1e j(θ+π / 2) ,b2e j(θ+π / 2) ,…,b N2 e j(θ+π / 2) , a1e j(θ+π) ,a2e j(θ+π) ,…,fence N2 by j(θ+π) , b1e j(θ+3π / 2) ,b2e j(θ+3π / 2) ,…,b N2 e j(θ+3π / 2) ; π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N2 and b1, b2, …, b N2 are all positive numbers and satisfy: 0<a1<a2<…<a N2 , 0<b1<b2<…<b N2 ; or, The modulation symbol is obtained by modulating M3+3 bits of information in the data packet according to a third constellation model, wherein the third constellation model includes 8*N3 constellation points, M3 is an integer greater than or equal to 0, and N3 and M3 satisfy the formula N3=2 M3 ; The complex forms corresponding to the 8*N3 constellation points in the third constellation diagram model include the following: a1e jθ ,a2e jθ ,…,fence N3 by jθ , a1e j(θ+π) ,a2e j(θ+π) ,…,fence N3 by j(θ+π) , π is the ratio of circumference to circumference; j is an imaginary number; the value of j is equal to e is the natural logarithm; θ is a real number; a1, a2,…, a N3 and b1, b2, …, b N3 are all positive numbers and satisfy: 0<a1<a2<…<a N3 , 0<b1<b2<…<b N3 .

18. The method according to claim 17, wherein: When the modulation symbol is modulated according to the first constellation model, a1, a2, ..., a N1 Both can be expressed by the following formula: a n =(2n-1+Δ)d; Alternatively, when the modulation symbol is modulated according to the second constellation model, a1, a2, ..., a N2 Both can be expressed by the following formula: a n =(2n-1+Δ)d; b1, b2, …, b N2 Both can be expressed by the following formula: b n =a n +b; Wherein, the value of n includes 1, 2, ..., N2; d is a positive real number, and Δ and β are both real numbers greater than or equal to 0; Alternatively, when the modulation symbol is modulated according to the third constellation model, a1, a2, ..., a N3 Both can be expressed by the following formula: a n =(2n-1+Δ)d; b1, b2, …, b N3 Both can be expressed by the following formula: b n =a n +b; Wherein, the value of n includes 1, 2, ..., N3; d is a positive real number, and Δ and β are both real numbers greater than or equal to 0.

19. The method according to claim 18, characterized in that The value of Δ is 0, and the value of d is 1, so that a n Satisfy a n =2n-1.

20. The method according to claim 18, wherein The value of Δ is 1, and the value of d is 1 / 2, so that a n Satisfy a n =n.

21. The method according to claim 18, wherein The value of Δ is 3, and the value of d is 1 / 2, so that a n Satisfy a n =n+1.

22. The method according to claim 18, wherein The value of Δ is 23. The method according to claim 22, wherein: The value of d is 1, so that a n satisfy Or, d takes the value of 1 / 2, so that a n satisfy 24. The method according to claim 18, wherein When the modulation symbol is modulated according to the second constellation model or the third constellation model, β is equal to 0.

25. The method according to claim 18, wherein When the modulation symbol is modulated according to the third constellation model, β is greater than 0.

26. The method according to claim 18, wherein: When the modulation symbol is modulated according to the first constellation model, the value of d is a value that makes the average power of the modulation symbol modulated by the first constellation model equal to 1; or, When the modulation symbol is modulated according to the second constellation model, the value of d is a value that makes the average power of the modulation symbol modulated by the second constellation model equal to 1; or, When the modulation symbol is modulated according to the third constellation model, the value of d is a value that makes the average power of the modulation symbol modulated by the third constellation model equal to 1.

27. The method according to claim 17, wherein: The value of θ is 0; or, The value of θ satisfies the formula θ=π / 4; or, The value of θ satisfies the formula θ=π / 8.

28. The method according to claim 17, wherein Each of the extremely sparse pilots includes a second number of non-zero value symbols, where the second number is greater than 0 and less than 5, and the second number of non-zero value symbols are carried on a third number of adjacent resource units in the time-frequency domain, or on a third number of symbols in chronological order, or on a third number of resource units on adjacent subcarriers in the frequency domain, wherein the third number is equal to the second number.

29. The method according to claim 17 or 28, characterized in that The symbol length of each of the extremely sparse pilots is greater than 24.

30. The method according to claim 28, wherein: The value of the second number is 1; or, The second number has a value of 2, and the second number of non-zero-valued symbols constitute a non-zero-valued symbol pair [p1, p2], and the value of [p1, p2] is [a1, a2] or [b1, b2], wherein [a1, a2] and [b1, b2] are orthogonal; or, The value of the second number is 2, and the second number of non-zero valued symbols constitutes a non-zero valued symbol pair [p1, p2], and the values ​​of [p1, p2] include at least the following situations: [p1, p2] = [1, 1]; [p1, p2] = [1, -1]; [p1, p2] = [1, j]; [p1, p2] = [1, -j]; or, The second number has a value of 4, and the second number of non-zero-valued symbols constitute a non-zero-valued symbol group [p1, p2, p3, p4], and the value of [p1, p2, p3, p4] is [a1, a2, a3, a4], [b1, b2, b3, b4], [c1, c2, c3, c4] or [d1, d2, d3, d4], wherein [a1, a2, a3, a4], [b1, b2, b3, b4], [c1, c2, c3, c4] and [d1, d2, d3, d4] are mutually orthogonal; or, The value of the second number is 4, and the second number of non-zero-valued symbols constitute a non-zero-valued symbol group [p1, p2, p3, p4], and the values ​​of [p1, p2, p3, p4] include at least the following cases: [p1, p2, p3, p4] = [1, 1, 1, 1]; [p1, p2, p3, p4] = [1, 1, -1, -1]; [p1, p2, p3, p4] = [1, -1, 1, -1]; [p1, p2, p3, p4] = [1, -1, -1, 1]; [p1, p2, p3, p4] = [1, 1, j, -j]; [p1, p2, p3, p4] = [1, 1, -j, j]; [p1, p2, p3, p4] = [1, -1, j, j]; [p1, p2, p3, p4] = [1, -1, -j, -j]; [p1, p2, p3, p4] = [1, j, 1, -j]; [p1, p2, p3, p4] = [1, j, -1, j]; [p1,p2,p3,p4]=[1,-j,1,j]; [p1,p2,p3,p4]=[1,-j,-1,-j]; [p1,p2,p3,p4]=[1,j,j,-1]; [p1,p2,p3,p4]=[1,j,-j,1]; [p1,p2,p3,p4]=[1,-j,j,1]; [p1,p2,p3,p4]=[1,-j,-j,-1]; [p1,p2,p3,p4]=[1,1,1,-1]; [p1,p2,p3,p4]=[1,1,-1,1]; [p1,p2,p3,p4]=[1,-1,1,1]; [p1,p2,p3,p4]=[1,-1,-1,-1]; [p1,p2,p3,p4]=[1,1,j,j]; [p1,p2,p3,p4]=[1,1,-j,-j]; [p1,p2,p3,p4]=[1,-1,j,-j]; [p1,p2,p3,p4]=[1,-1,-j,j]; [p1,p2,p3,p4]=[1,j,1,j]; [p1,p2,p3,p4]=[1,j,-1,-j]; [p1,p2,p3,p4]=[1,-j,1,-j]; [p1,p2,p3,p4]=[1,-j,-1,j]; [p1,p2,p3,p4]=[1,j,j,1]; [p1,p2,p3,p4]=[1,j,-j,-1]; [p1,p2,p3,p4]=[1,-j,j,-1]; [p1,p2,p3,p4]=[1,-j,-j,1]; [p1,p2,p3,p4]=[1,1,1,j]; [p1,p2,p3,p4]=[1,1,-1,-j]; [p1,p2,p3,p4]=[1,-1,1,-j]; [p1,p2,p3,p4]=[1,-1,-1,j]; [p1,p2,p3,p4]=[1,1,j,1]; [p1,p2,p3,p4]=[1,1,-j,-1]; [p1,p2,p3,p4]=[1,-1,j,-1]; [p1,p2,p3,p4]=[1,-1,-j,1]; [p1,p2,p3,p4]=[1,j,1,1]; [p1,p2,p3,p4]=[1,j,-1,-1]; [p1,p2,p3,p4]=[1,-j,1,-1]; [p1,p2,p3,p4]=[1,-j,-1,1]; [p1,p2,p3,p4]=[1,j,j,-j]; [p1,p2,p3,p4]=[1,j,-j,j]; [p1,p2,p3,p4]=[1,-j,j,j]; [p1,p2,p3,p4]=[1,-j,-j,-j]; [p1,p2,p3,p4]=[1,1,1,-j]; [p1, p2, p3, p4] = [1, 1, -1, j]; [p1, p2, p3, p4] = [1, -1, 1, j]; [p1, p2, p3, p4] = [1, -1, -1, -j]; [p1, p2, p3, p4] = [1, 1, j, -1]; [p1, p2, p3, p4] = [1, 1, -j, 1]; [p1, p2, p3, p4] = [1, -1, j, 1]; [p1, p2, p3, p4] = [1, -1, -j, -j]; [p1, p2, p3, p4] = [1, j, 1, -1]; [p1, p2, p3, p4] = [1, j, -1, 1]; [p1, p2, p3, p4] = [1, -j, 1, 1]; [p1, p2, p3, p4] = [1, -j, -1, -1]; [p1, p2, p3, p4] = [1, j, j, j]; [p1, p2, p3, p4] = [1, j, -j, -j]; [p1, p2, p3, p4] = [1, -j, j, -j]; [p1, p2, p3, p4] = [1, -j, -j, j].

31. The method according to claim 17, wherein When the value of the first number is greater than or equal to 2: The first number of extremely sparse pilots are independent of each other; or, The first number of the extremely sparse pilots is determined according to information in the data packet; or, The first number of the extremely sparse pilots is determined according to one or more bits of information in the data packet; or, Each of the extremely sparse pilots is determined from a preset pilot set based on a fourth number of bit information in the data packet, wherein the preset pilot set includes a fifth number of pilots, the fourth number is in a logarithmic function relationship with the fifth number, and the logarithmic function is a logarithmic function with base 2.

32. The method according to claim 17, wherein The value of the first number is 1 or 2.

33. A communication device, characterized in that: include: at least one processor; at least one memory for storing at least one program; When at least one of the programs is executed by at least one of the processors, the information transmission method according to any one of claims 1 to 32 is implemented.

34. A computer-readable storage medium storing computer-executable instructions, wherein the computer-executable instructions are used to execute the information transmission method according to any one of claims 1 to 32.

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