Power amplifier circuit, communication module and communication equipment

Abstract

The embodiments of the present application provide a power amplifier circuit, a communication module and a communication device, and relate to the field of terminal technology. The power amplifier circuit includes: a power divider, a coupling unit, a first reactance unit, a first power amplifier unit and a signal amplifier unit; the power divider is used to decompose the radio frequency signal into a first signal and a second signal, and the first signal is transmitted to the control end of the signal amplifier unit via the input port, the isolation port and the first power amplifier unit of the coupling unit, so that the load impedance of the signal amplifier unit is negatively correlated with the input power of the radio frequency signal when the power is backed off. The second signal is output after being amplified by the signal amplifier unit; wherein the phase shift of the first signal in the coupling unit is related to the reactance at the fourth port; the first reactance unit is used to adjust the reactance at the fourth port. In this way, the phase adjustment and amplitude adjustment of the first signal are decoupled by the coupling unit and the reactance unit, reducing the design difficulty and debugging difficulty of the power amplifier circuit.

Description

Technical Field

[0001] The present application relates to the field of terminal technology, and in particular to a power amplifier circuit, a communication module and a communication device. Background Art

[0002] To improve spectrum utilization and communication reliability, the modulation methods of RF signals are becoming more and more complex, and the peak-to-average power ratio (PAPR) of RF signals is getting higher and higher. To meet the linearity requirements when amplifying RF signal power, the power amplifier usually works in a power back-off state.

[0003] Compared with a conventional power amplifier circuit composed of a power amplifier of a single structure (for example, only including a class AB power amplifier), the power amplifier circuit of the load modulation structure has a higher efficiency in a power back-off state.

[0004] However, it is difficult to debug the power amplifier circuit with load modulation structure. Summary of the invention

[0005] The embodiment of the present application provides a power amplifier circuit, a communication module and a communication device, which are applied to the field of terminal technology. A coupler is applied to a power amplifier circuit with a load modulation structure to reduce the difficulty of debugging the power amplifier circuit.

[0006] In the first aspect, an embodiment of the present application proposes a power amplifier circuit. The power amplifier circuit includes: a power divider, a first coupling unit, a first reactance unit, a first power amplification unit and a signal amplification unit; the power divider includes: a first port, a second port and a third port; the first coupling unit includes: a first input port, a first isolation port, a fourth port and a fifth port; the first port is used to input a radio frequency signal, the second port is connected to the first input port, the first isolation port is connected to the input end of the first power amplification unit, and the output end of the first power amplification unit is connected to the control end of the signal amplification unit; the fourth port is connected to one end of the first reactance unit, and the other end of the first reactance unit is grounded; the fifth port is grounded; the third port is connected to the input end of the signal amplification unit, and the signal amplification unit is connected to the control end of the signal amplification unit; The output end of the unit is used to output the amplified RF signal; the power divider is used to decompose the RF signal into a first signal and a second signal at the first port; wherein the second port is used to output the first signal, and the third port is used to output the second signal; the first coupling unit is also used to adjust the phase of the first signal; wherein the phase shift of the first signal at the first coupling unit is related to the reactance at the fourth port; the first reactance unit is used to adjust the reactance at the fourth port; the first power amplification unit is used to amplify the first signal; the signal amplification unit is used to amplify the second signal; wherein the load impedance of the signal amplification unit is negatively correlated with the input power of the RF signal when the power is backed off under the control of the first signal at the input control end.

[0007] The first signal may correspond to signal A hereinafter, and the second signal may correspond to signal B hereinafter.

[0008] The phase of the first signal is adjusted by the first coupling unit and the first reactance unit, thereby realizing load modulation of the signal amplification unit. In the process of adjusting the phase shift of the first signal in the first coupling unit by the first reactance unit, the amplitude of the first signal changes slightly. In this way, the phase shift change and loss change of the signal in the first coupling unit are decoupled, the influence of the phase modulation of the signal on the amplitude modulation of the signal is reduced, the difficulty of predicting the load impedance change of the signal amplification unit is reduced, and the design difficulty and debugging difficulty of the power amplifier circuit of the load modulation structure are reduced.

[0009] In a possible implementation manner, the first reactance unit includes: a first capacitor.

[0010] In this way, the reactance adjustment of the first reactance unit can be achieved by replacing the capacitor. The capacitor element is easy to disassemble and convenient for debugging.

[0011] In one possible implementation, the power amplifier circuit also includes: a second reactance unit, the fifth port is connected to one end of the second reactance unit, and the other end of the second reactance unit is grounded; the second reactance unit is used to adjust the reactance at the fifth port to reduce the insertion loss of the first coupling unit.

[0012] In this way, the first signal may also include a signal reflected by the fifth port, which may reduce the insertion loss of the first coupling unit.

[0013] In a possible implementation manner, a difference between a reactance value of the first reactance unit and a reactance value of the second reactance unit is smaller than a preset threshold.

[0014] In this way, the reactance of the first reactance unit is close to or even the same as the reactance of the second reactance unit, which can reduce the phase difference between the signal reflected from the coupling port to the isolation port and the phase difference between the signal reflected from the through port to the isolation port, thereby reducing the insertion loss of the first coupling unit.

[0015] In a possible implementation, the first reactance unit includes: a first capacitor, the second reactance unit includes: a second capacitor, and a difference between a capacitance value of the first capacitor and a capacitance value of the second capacitor is less than a preset threshold.

[0016] In this way, the reactance adjustment of the first reactance unit and the reactance adjustment of the second reactance unit can be achieved by replacing the capacitor. The capacitor element is easy to disassemble and convenient for debugging.

[0017] In a possible implementation, the power amplifier circuit also includes: a phase compensation unit, which is located between the power divider and the signal amplification unit; the phase compensation unit is used to adjust the phase of the second signal so that the absolute value of the difference between the first phase difference and the second phase difference is less than or equal to the first threshold; the first phase difference is the difference between the phase of the first signal at the first port and the phase of the second signal at the other end of the phase compensation unit when the RF signal is the first frequency; the second phase difference is the difference between the phase of the first signal at the first port and the phase of the second signal at the other end of the phase compensation unit when the RF signal is the second frequency.

[0018] The first threshold value may be 1, 5 or any value, which is not specifically limited here.

[0019] The phase compensation unit can compensate for the difference in phase adjustment of the first coupling unit for signals of different frequencies, so that when the power amplifier circuit amplifies signals of different frequencies, the phase difference between the first signal output by the first coupling unit and the second signal output by the phase compensation unit is maintained within a preset range. In this way, broadband phase shifting of the power amplifier circuit can be achieved.

[0020] In a possible implementation, the signal amplification unit includes: a second coupling unit, a second power amplification unit, a third power amplification unit and a third coupling unit; the second coupling unit includes: a second input port, a second isolation port, a sixth port and a seventh port; the third coupling unit includes: a third input port, a third isolation port, an eighth port and a ninth port; the second input port is the input end of the signal amplification unit, the second isolation port is grounded, the sixth port is connected to the input end of the second power amplification unit, and the output end of the second power amplification unit is connected to the eighth port; the seventh port is connected to the input end of the third power amplification unit, the output end of the third power amplification unit is connected to the ninth port, the third isolation port is the control end of the signal amplification unit, and the third input port is used to output the amplified radio frequency signal; the second coupling unit is used to decompose the second signal into a third signal and a fourth signal; the second power amplification unit is used to amplify the third signal; the third power amplification unit is used to amplify the fourth signal; the third coupling unit is used to combine the third signal and the fourth signal under the control of the first signal to obtain the amplified radio frequency signal.

[0021] In this way, power amplification of the second signal can be achieved through two coupling units and two power amplification units, and the first signal can achieve load modulation on the signal amplification unit when power is backed off.

[0022] In the second aspect, the embodiment of the present application proposes a power amplifier circuit. The power amplifier circuit includes: a first coupling unit, a first reactance unit, a first power amplifier unit and a signal amplifier unit; the first coupling unit includes: a first input port, a first isolation port, a fourth port and a fifth port; the first input port is used to input a radio frequency signal, the first isolation port is connected to the input end of the first power amplifier unit, and the output end of the first power amplifier unit is connected to the control end of the signal amplifier unit; the fourth port is connected to one end of the first reactance unit, and the other end of the first reactance unit is grounded; the fifth port is connected to the input end of the signal amplifier unit, and the output end of the signal amplifier unit is used to output the amplified radio frequency signal; the first coupling unit is used to decompose the radio frequency signal into a first signal and a second signal at the first input port; wherein the first isolation port is used to output the first signal, and the fifth port is used to output the second signal; the phase shift of the first signal at the first coupling unit is related to the reactance at the fourth port; the first reactance unit is used to adjust the reactance at the fourth port; the first power amplifier unit is used to amplify the first signal; the signal amplifier unit is used to amplify the second signal; the load impedance of the signal amplifier unit is negatively correlated with the input power of the radio frequency signal under the control of the first signal at the input control end when the power is backed off.

[0023] The first signal may correspond to signal A hereinafter, and the second signal may correspond to signal B hereinafter.

[0024] The RF signal can be divided into a first signal and a second signal by the first coupling unit, and the first signal is phase-adjusted in the first coupling unit, thereby realizing load modulation of the signal amplification unit. In the process of adjusting the phase shift of the first signal in the first coupling unit by the first reactance unit, the amplitude of the first signal changes slightly. In this way, the phase shift change and loss change of the signal in the first coupling unit are decoupled, the influence of the phase modulation of the signal on the amplitude modulation of the signal is reduced, the difficulty of predicting the load impedance change of the signal amplification unit is reduced, and the design difficulty and debugging difficulty of the power amplifier circuit of the load modulation structure are reduced.

[0025] In a possible implementation manner, the first reactance unit includes: a first capacitor.

[0026] In this way, the reactance adjustment of the first reactance unit can be achieved by replacing the capacitor. The capacitor element is easy to disassemble and convenient for debugging.

[0027] In a possible implementation, the power amplifier circuit also includes: a phase compensation unit, which is located between the first coupling unit and the signal amplification unit; a phase compensation unit, which is used to adjust the phase of the second signal so that the absolute value of the difference between the first phase difference and the second phase difference is less than or equal to the first threshold; the first phase difference is the difference between the phase of the first signal at the first port and the phase of the second signal at the other end of the phase compensation unit when the RF signal is a first frequency; the second phase difference is the difference between the phase of the first signal at the first port and the phase of the second signal at the other end of the phase compensation unit when the RF signal is a second frequency.

[0028] The first threshold value may be 1, 5 or any value, which is not specifically limited here.

[0029] The phase compensation unit can compensate for the difference in phase adjustment of the first coupling unit for signals of different frequencies, so that when the power amplifier circuit amplifies signals of different frequencies, the phase difference between the first signal output by the first coupling unit and the second signal output by the phase compensation unit is maintained within a preset range. In this way, broadband phase shifting of the power amplifier circuit can be achieved.

[0030] In a third aspect, an embodiment of the present application provides a communication module. The communication module includes: a radio frequency integrated circuit, and a power amplifier circuit in the first aspect, any possible implementation of the first aspect, the second aspect, or any possible implementation of the second aspect; the radio frequency integrated circuit is used to output a radio frequency signal; and the power amplifier circuit is used to amplify the radio frequency signal.

[0031] In a fourth aspect, an embodiment of the present application provides a communication device. The communication device includes: an antenna and a communication module in the third aspect or any possible implementation of the third aspect;

[0032] The communication module is used to output the amplified radio frequency signal to the antenna; the antenna is used to transmit the amplified radio frequency signal.

[0033] It should be understood that the third aspect and the fourth aspect of the present application correspond to the technical solution of the first aspect or the technical solution of the second aspect of the present application, and the beneficial effects achieved by each aspect and the corresponding feasible implementation methods are similar and will not be repeated. BRIEF DESCRIPTION OF THE DRAWINGS

[0034] Figure 1 A schematic diagram of the relationship between power back-off and efficiency provided in an embodiment of the present application;

[0035] Figure 2 A schematic diagram of a load impedance change of a power amplifier provided in an embodiment of the present application;

[0036] Figure 3A schematic diagram of the structure of a LMBA in a possible design;

[0037] Figure 4 Schematic diagram of phase shift change and insertion loss change of signal A in possible designs;

[0038] Figure 5 A schematic diagram of the structure of a power amplifier circuit provided in an embodiment of the present application;

[0039] Figure 6 A schematic diagram of the phase shift of the signal A and the insertion loss change of the coupling unit 402 when the capacitance C2 changes according to an embodiment of the present application;

[0040] Figure 7 A schematic diagram of the structure of a power amplifier circuit provided in an embodiment of the present application;

[0041] Figure 8 A schematic diagram of the structure of a phase compensation unit provided in an embodiment of the present application;

[0042] Fig. 9 A schematic diagram of a change in the difference between the phase of a signal A output by a coupling unit 402 and the phase of a signal B input to a coupling unit 406 provided in an embodiment of the present application;

[0043] Fig.10 A schematic diagram of the structure of another power amplifier circuit provided in an embodiment of the present application;

[0044] Fig.11 A schematic diagram of a phase shift of a signal A and a loss change of the signal A transmitted in a coupling unit 902 when a capacitance C4 changes provided in an embodiment of the present application;

[0045] Fig.12 A schematic diagram of phase shift and insertion loss of signal B in coupling unit 902 provided in an embodiment of the present application;

[0046] Fig.13 A schematic diagram of the structure of a power amplifier circuit provided in an embodiment of the present application;

[0047] Fig.14 A schematic diagram of the structure of an electronic device provided in an embodiment of the present application;

[0048] Fig.15 A schematic diagram of the structure of a communication module provided in an embodiment of the present application. DETAILED DESCRIPTION

[0049] In order to clearly describe the technical solutions of the embodiments of the present application, some of the terms and technologies involved in the embodiments of the present application are briefly introduced below:

[0050] Power amplifier (PA)

[0051] By amplifying the voltage and current of the input signal, the power output of the signal is increased. Or it can be understood as power amplification of the RF signal.

[0052] It should be noted that the working state of the power amplifier can be divided into a linear region and a nonlinear region. In the linear region, the output power of the power amplifier increases linearly with the increase of the input power; when the input power of the power amplifier further increases, the power amplifier enters the nonlinear region, the output power of the power amplifier no longer increases with the increase of the input power, and the output power of the power amplifier reaches saturation, at which time, the efficiency of the power amplifier is the highest.

[0053] According to the type of power amplifier, PA can be divided into: Class A power amplifier, Class B power amplifier, Class AB power amplifier or Class C power amplifier, etc.

[0054] Among them, the Class A power amplifier is in the on state during the entire input signal cycle. When there is no input signal (it can also be understood that the power of the input signal is zero), the Class A amplifier will also consume DC power. It can also be understood that the conduction angle of the Class A power amplifier is 360 degrees.

[0055] The Class B power amplifier uses two amplifier elements in the positive half cycle and negative half cycle of the input signal, one for the positive half cycle and the other for the negative half cycle. When there is no input signal (it can also be understood that the power of the input signal is zero), the two elements are in the cut-off state. It can also be understood that the conduction angle of the Class B power amplifier is 180 degrees.

[0056] Class C power amplifiers are turned on for a small portion of the input signal cycle, usually less than 50% of the time. The operating point of a Class C amplifier is usually set near the cutoff region. It can also be understood that the conduction angle of a Class C power amplifier is less than 180 degrees.

[0057] The class AB power amplifier combines the characteristics of class A and class B amplifiers. The two amplifier elements are turned on in the positive and negative half cycles of the input signal, but there is a certain overlap of conduction time near the zero crossing point. It can also be understood that the conduction angle of the class AB power amplifier is between 180 degrees and 360 degrees.

[0058] It can be understood that the Class A power amplifier is suitable for the scenario where the RF signal is a small signal, the Class B power amplifier and the Class C power amplifier are suitable for the scenario where the RF signal is a large signal, and the Class AB power amplifier is equivalent to the Class A power amplifier when the RF signal is a small signal, and is equivalent to the Class B power amplifier when the RF signal is a large signal. Among them, the small signal refers to the RF signal input to the power amplifier with a small power, and the large signal refers to the RF signal input to the power amplifier with a large power.

[0059] 3. Power amplifier efficiency

[0060] The efficiency of a power amplifier is used to indicate the ability of the power amplifier to convert input power into output power. For example, the efficiency of a power amplifier may be a ratio of the output power of the power amplifier to the input power.

[0061] 4. Power backoff

[0062] Power back-off can be to reduce the output power of the power amplifier to below its maximum output power, or it can be understood as reducing the critical point between the linear region and the nonlinear region of the power amplifier (for example, the 1dB compression point of the power amplifier) ​​by a certain amplitude (for example, 6dB, 10dB, etc.).

[0063] In some embodiments, the power backoff is quantified in decibels (dB) to indicate the magnitude of the output power reduction. For example, if the maximum output power of a power amplifier is 30 decibel milliwatts (dBm) and the power backoff is 3 dB, the output power is reduced to 27 dBm.

[0064] 5. Nonlinear distortion

[0065] Nonlinear distortion can be understood as the nonlinear relationship between the signal output by the nonlinear device and the signal input to the nonlinear device when the signal passes through the nonlinear device (for example, a power amplifier), resulting in signal distortion.

[0066] 6. Other terms

[0067] In the embodiments of the present application, words such as "first" and "second" are used to distinguish the same or similar items with substantially the same functions and effects. For example, the first chip and the second chip are only used to distinguish different chips, and their order is not limited. Those skilled in the art can understand that words such as "first" and "second" do not limit the quantity and execution order, and words such as "first" and "second" do not necessarily limit them to be different.

[0068] It should be noted that in the embodiments of the present application, words such as "exemplary" or "for example" are used to indicate examples, illustrations or descriptions. Any embodiment or design described as "exemplary" or "for example" in the present application should not be interpreted as being more preferred or more advantageous than other embodiments or designs. Specifically, the use of words such as "exemplary" or "for example" is intended to present related concepts in a specific way.

[0069] In the embodiments of the present application, "at least one" refers to one or more, and "more than one" refers to two or more. "And / or" describes the association relationship of associated objects, indicating that three relationships may exist. For example, A and / or B can represent: the existence of A alone, the existence of A and B at the same time, and the existence of B alone, where A and B can be singular or plural. The character " / " generally indicates that the previous and next associated objects are in an "or" relationship. "At least one of the following" or similar expressions refers to any combination of these items, including any combination of single or plural items. For example, at least one of a, b, or c can represent: a, b, c, ab, a--c, bc, or abc, where a, b, and c can be single or multiple.

[0070] 7. Electronic devices

[0071] The electronic device of the embodiment of the present application may include a handheld device, a vehicle-mounted device, etc. with a signal transmission function. For example, some electronic devices are: mobile phones, tablet computers, PDAs, laptop computers, mobile internet devices (MIDs), wearable devices (e.g., smart watches, smart glasses, smart bracelets, or smart jewelry, etc.), virtual reality (VR) devices, augmented reality (AR) devices, wireless terminals in industrial control, wireless terminals in self driving, wireless terminals in remote medical surgery, wireless terminals in smart grids, wireless terminals in transportation safety, wireless terminals in smart cities, wireless terminals in smart homes, cellular phones, cordless phones, session initiation protocol (SIP) phones, wireless local loop (WLL) stations, personal digital assistants (PDAs), handheld devices with wireless communication capabilities, computing devices or other processing devices connected to wireless modems, vehicle-mounted devices, Internet of Things (IoT), and the like. The present invention relates to terminal devices in an Internet of Things (IoT) system, terminal devices in a 5G network, or terminal devices in a future evolved public land mobile network (PLMN), etc., and the embodiments of the present application are not limited to this.

[0072] The electronic device in the embodiments of the present application may also be referred to as: terminal equipment, user equipment (UE), mobile station (MS), mobile terminal (MT), access terminal, user unit, user station, mobile station, mobile station, remote station, remote terminal, mobile device, user terminal, terminal, wireless communication equipment, user agent or user device, etc.

[0073] In order to improve the utilization of spectrum and the reliability of communication, the modulation method of RF signals in communication systems is becoming more and more complex, which increases the peak-to-average ratio of RF signals. The increase in the peak-to-average ratio may cause the power amplifier in the power amplifier circuit to operate in a nonlinear region, which in turn causes nonlinear distortion of the power amplifier circuit.

[0074] The power back-off method is adopted to reduce the power amplifier in the power amplifier circuit from entering the nonlinear region and reduce the nonlinear distortion.

[0075] However, in the power back-off state, the efficiency of the conventional power amplifier circuit (eg, including only a class AB power amplifier) ​​is low. The conventional power amplifier circuit is composed of a power amplifier of a single structure, for example, the conventional power amplifier circuit includes only a class AB power amplifier.

[0076] For example, Figure 1 A schematic diagram of the relationship between power back-off and efficiency provided in an embodiment of the present application. Taking a conventional power amplifier circuit including a class B power amplifier or a class AB power amplifier as an example, the efficiency change of the class B power amplifier under different power back-off values ​​can be as follows: Figure 1 As shown in the curve 101 in FIG. 1 , the efficiency change of the class AB power amplifier at different power back-off values ​​can be shown as follows: Figure 1 As shown by curve 102 in FIG.

[0077] from Figure 1 It can be seen that the efficiency of the conventional power amplifier circuit is negatively correlated with the power back-off value. The higher the power back-off value, the lower the efficiency of the power amplifier.

[0078] It is understandable that in the power fallback state, the efficiency of conventional power amplifier circuits is low and the power consumption of the power amplifier circuits is high. In addition, the power amplifier circuits may emit a large amount of heat in the low efficiency state, which puts great pressure on the heat dissipation of electronic equipment. When the power amplifier circuit works at low efficiency for a long time, it may be damaged by overheating due to untimely heat dissipation, and the life of the power amplifier circuit is reduced.

[0079] In some embodiments, the electronic device uses a power amplifier circuit with a load modulation structure to amplify the RF signal. Specifically, the power amplifier circuit with a load modulation structure can divide the RF signal into signal A and signal B. Signal A can adjust the phase and amplitude of the signal through the control signal unit, and signal B is amplified (power amplified) through the signal amplification unit. After adjusting the phase and amplitude, signal A can be input into the signal amplification unit from the control end of the signal amplification unit, so that the load impedance of the signal amplification unit is negatively correlated with the input power of the RF signal when the power is backed off, thereby improving the efficiency of the signal amplification unit and the efficiency of the power amplifier circuit.

[0080] Taking a load modulated balanced power amplifier (LMBA) as an example, the power amplifier circuit of the load modulation structure includes a power amplifier CA, and the signal amplification unit of the LMBA includes an input coupler, two power amplifiers BA and an output coupler.

[0081] In a possible design, the working principle of the LMBA is as follows: the signal A can be transmitted to the isolation port of the output coupler after being amplified by the power amplifier CA.

[0082] Signal B can be decomposed into two orthogonal signals with equal amplitude (90 degrees phase difference) through the input coupler. The two orthogonal signals are amplified by corresponding power amplifiers BA respectively and transmitted to the through port and coupled port of the output coupler.

[0083] By reasonably designing the size (also understood as amplitude) and phase of the signal A transmitted to the isolation port of the output coupler, it is possible to modulate the load impedance of the two power amplifiers BA, and realize the load impedance modulation of the signal amplification unit by the signal A transmitted by the control unit, thereby improving the efficiency of the LMBA.

[0084] It should be noted that the load impedance of the power amplifier is equal to the ratio of the output voltage to the output current, such as Figure 2 As shown in a, when the load impedance of the power amplifier remains unchanged (that is, the slope of the output voltage / output current remains unchanged), when the output current of the power amplifier is small, the output voltage is also small. At this time, the efficiency of the power amplifier is low. Figure 2 As shown in b, when the output current of the power amplifier is small, the output voltage of the power amplifier can be increased by increasing the load impedance of the power amplifier, making it easier for the power amplifier to enter the saturation region in advance, thereby improving the efficiency of the power amplifier.

[0085] It can be understood that, compared with the conventional power amplifier structure, the efficiency of the power amplifier circuit with load modulation structure is higher in the back-off state. For example, taking the power amplifier circuit with load modulation structure as LMBA as an example, the efficiency change of LMBA under different power back-off can be as follows: Figure 1 As shown in curve 103, when the power backoff value is less than -10dB, the efficiency of LMBA gradually increases as the power backoff decreases; when the power backoff is -10dB, the efficiency of LMBA reaches the highest; when the power backoff is between -10dB and 0dB, the efficiency of LMBA first decreases and then increases as the power backoff decreases.

[0086] from Figure 1 It can be seen that compared with conventional power amplifier circuits, LMBA has higher efficiency in the power back-off state.

[0087] However, it is difficult to design a power amplifier circuit with a load modulation structure in a possible design.

[0088] For example, taking the power amplifier circuit of the load modulation structure as LMBA as an example, Figure 3 Figure 1 is a schematic diagram of the structure of a possible LMBA design. Figure 3 As shown, the LMBA includes: a power divider 201, an LC phase shift unit 202, a power amplifier 203, a coupler 204, a power amplifier 205, a power amplifier 206, and a coupler 207. The control unit may include: an LC phase shift unit 202 and a power amplifier 203; the signal amplification unit may include: a coupler 204, a power amplifier 205, a power amplifier 206, and a coupler 207.

[0089] The power divider 201 includes: port 1a, port 1b and port 1c; the coupler 204 includes: input port 2a, coupling port 2b, through port 2c and isolation port 2d; the coupler 207 includes: input port 3a, coupling port 3b, through port 3c and isolation port 3d.

[0090] like Figure 3As shown, port 1a of power divider 201 is used to input RF signal; port 1b of power divider 201 is connected to one end of LC phase shift unit 202, and port 1c of power divider 201 is connected to input port 2a of coupler 204. The other end of LC phase shift unit 202 is connected to the input end of power amplifier 203, and the output end of power amplifier 203 is connected to isolation port 3d of coupler 207; coupling port 2b of coupler 204 is connected to the input end of power amplifier 205, and the output end of power amplifier 205 is connected to through port 3c of coupler 207; through port 2c of coupler 204 is connected to the input end of power amplifier 206, and the output end of power amplifier 206 is connected to isolation port 3d of coupler 207; input port 3a of coupler 207 is used to output amplified RF signal, and isolation port 2d of coupler 204 is grounded.

[0091] Figure 3 In the circuit shown, the power divider 201 can divide the radio frequency signal input to the LMBA into two signals, and the two signals are processed by the control signal unit and the signal amplification unit respectively.

[0092] Taking the example of the power divider 201 dividing the RF signal into signal A and signal B, signal A is phase-adjusted by the LC phase shift unit 202 , amplified by the power amplifier 203 , and transmitted to the isolation port 3 d of the coupler 207 .

[0093] Signal B is decomposed into signal b1 and signal b2 by coupler 204. Signal b1 is amplified by power amplifier 205 and transmitted to through port 3c of coupler 207; signal b2 is amplified by power amplifier 206 and transmitted to coupling port 3b of coupler 207. Signal b1 and signal b2 have equal amplitudes and are orthogonal (the phase difference between signal b1 and signal b2 is 90 degrees).

[0094] The amplified signal A, the amplified signal b1 and the amplified signal b2 are combined into one signal output by the coupler 207 .

[0095] It should be noted that the impedance of the through port 3 c of the coupler 207 and the impedance of the coupled port 3 b of the coupler 207 are both controlled by the amplified signal A. It can also be understood that the impedance of the through port 3 c of the coupler 207 and the impedance of the coupled port 3 b of the coupler 207 are both related to the amplitude and phase of the amplified signal A.

[0096] It is understandable that the above Figure 3 In the LMBA shown, the amplitude and phase of the amplified signal A are controlled by adjusting the LC phase shift unit 202, thereby achieving dynamic load matching of the signal amplification unit.

[0097] However, in the process of adjusting the LC phase shift unit 202, the phase shift of signal A in the LC phase shift unit and the loss of signal A in the LC phase shift unit will change, and thus the phase and amplitude of the amplified signal A will change. Since the phase and amplitude of the amplified signal A change, it is difficult to predict the load impedance change of the signal amplification unit, dynamic load matching is difficult to achieve, and the design of LMBA is difficult.

[0098] In the embodiment of the present application, the phase shift of the signal in the LC phase shift unit can be understood as the difference between the phase of the signal output by the LC phase shift unit and the phase of the signal input to the LC phase shift unit. The loss of the signal in the LC phase shift unit can also be called the insertion loss of the LC phase shift unit.

[0099] For example, Figure 3 Taking the LC phase shift unit 202 shown as including an inductor and a capacitor as an example, when the capacitance value of the capacitor C1 is adjusted, the phase of the amplified signal A changes, causing the load impedance of the signal amplification unit to change; in addition, the insertion loss of the LC phase shift unit 202 fluctuates greatly, and the amplitude of the amplified signal A will also change, causing the load impedance of the signal amplification unit to change.

[0100] By way of example, taking the RF signal as an N77 signal with a frequency range of 3.3 GHz to 4.2 GHz, the inductance value of the inductor L1 as 0.7 nanohenry (nH), and the capacitance values ​​of the capacitor C1 as 0.5 picofarads (pF) and 0.9 pF, the insertion loss of the LC phase shift unit 202 and the phase shift of the signal A in the LC phase shift unit 202 are described.

[0101] like Figure 4 As shown, in the scenario where the capacitor C1 is 0.5 pf, the phase shift of the signal A in the LC phase shift unit can be as follows: Figure 4 As shown in curve 301 in a of FIG. 1 ; in the scenario where the capacitor C1 is 0.9 pf, the phase shift of the signal A in the LC phase shift unit can be as follows Figure 4 As shown in curve 302 in a of FIG. 1 ; in the scenario where the capacitance C1 is 0.5 pf, the insertion loss of the LC phase shift unit can be as follows Figure 4 As shown in curve 303 in b of FIG. 1 ; in the scenario where the capacitance C1 is 0.9 pf, the insertion loss of the LC phase shift unit can be as follows Figure 4 As shown in curve 304 in b.

[0102] from Figure 4 It can be seen that if the capacitance value is adjusted from 0.5pf to 0.9pf, the phase shift of signal A in the LC phase shift unit changes between 10 degrees and 15 degrees, and the insertion loss of the LC phase shift unit changes between 0.4dB and 0.7dB.

[0103] Combination Figure 3 and Figure 4 It can be seen that when the capacitance value of capacitor C1 changes, the phase shift of signal A in the LC phase shift unit and the insertion loss of the LC phase shift unit will change. It can also be understood that in the process of adjusting the phase of signal A by adjusting the capacitance value of capacitor C1, the insertion loss of the LC phase shift unit changes, causing the amplitude of the amplified signal A to change, and then the change of the load impedance of the signal amplification unit is difficult to predict, and the design and debugging of LMBA are difficult.

[0104] It is understandable that the above Figure 3 The LC phase shift unit 202 shown is only an example. When the LC phase shift unit 202 can be more complex, the undecoupled relationship between the amplitude and phase of the amplified signal A makes the design of the LMBA difficult, the design time is long, and the debugging is difficult.

[0105] In view of this, the embodiments of the present application provide a power amplifier circuit, a communication module and a communication device. The phase adjustment of the signal transmitted in the control signal unit is achieved through a coupler. Specifically, the isolation port of the coupler is connected to the power amplifier in the control signal unit, and a reactance unit is set at the through port or the coupled port of the coupler to achieve the phase adjustment of the signal output from the isolation port.

[0106] It should be noted that in the process of adjusting the phase of the signal output from the isolation port through the reactance unit, the insertion loss of the coupler changes slightly, so that the amplitude of the signal output from the isolation port changes slightly. In this way, the phase shift change of the signal in the control signal unit and the insertion loss change of the control signal unit (also called the loss change of the signal) are decoupled, reducing the influence of the phase modulation of the signal on the amplitude modulation of the signal, reducing the difficulty of predicting the load impedance change of the signal amplification unit, and reducing the design difficulty and debugging difficulty of the power amplifier circuit with the load modulation structure.

[0107] For example, Figure 5 This is a schematic diagram of the structure of a power amplifier circuit provided in an embodiment of the present application. Figure 5 As shown, the power amplifier includes: a power divider 401, a coupling unit 402, a power amplifying unit 403, a reactance unit 404, a reactance unit 405, a coupling unit 406, a power amplifying unit 407, a power amplifying unit 408 and a coupling unit 409.

[0108] Among them, the power divider 401 includes: port 4a, port 4b and port 4c; the coupling unit 402 includes: input port 5a, coupling port 5b, through port 5c and isolation port 5d; the coupling unit 406 includes: input port 6a, coupling port 6b, through port 6c and isolation port 6d; the coupling unit 409 includes: input port 7a, coupling port 7b, through port 7c and isolation port 7d.

[0109] like Figure 5 As shown, port 4a of the power divider 401 is used to input a radio frequency signal; port 4b of the power divider 401 is connected to input port 5a of the coupling unit 402 , and port 4c of the power divider 401 is connected to input port 6a of the coupling unit 406 .

[0110] The isolation port 5d of the coupling unit 402 is connected to the input end of the power amplification unit 403, and the output end of the power amplification unit 403 is connected to the isolation port 7d of the coupling unit 409; the through port 5c of the coupling unit 402 is connected to one end of the reactance unit 404, and the other end of the reactance unit 404 is grounded; the coupling port 5b of the coupling unit 402 is connected to one end of the reactance unit 405, and the other end of the reactance unit 405 is grounded.

[0111] The coupling port 6b of the coupling unit 406 is connected to the input end of the power amplifier unit 407, and the output end of the power amplifier unit 407 is connected to the straight-through port 7c of the coupling unit 409; the straight-through port 6c of the coupling unit 406 is connected to the input end of the power amplifier unit 408, and the output end of the power amplifier unit 408 is connected to the isolation port 7d of the coupling unit 409; the input port 7a of the coupling unit 409 is used to output the amplified RF signal, and the isolation port 6d of the coupling unit 406 is grounded.

[0112] In the embodiment of the present application, the power divider 401 is used to divide the radio frequency signal into two paths, namely signal A and signal B. The power of signal A and signal B may be the same or different, which is not specifically limited here.

[0113] The coupling unit 402 is used to adjust the phase of the signal A. The phase shift of the signal A in the coupling unit 402 is related to the reactance of the reactance unit 404 and the reactance of the reactance unit 405. Specifically, when the reactance of the reactance unit 404 or the reactance of the reactance unit 405 changes, the phase shift of the signal A in the coupling unit 402 also changes.

[0114] It should be noted that, based on the coupling effect of the electromagnetic field, the coupling line in the coupler can couple the signal transmitted by the transmission line in the coupler, and output the coupled signal from the coupling port; output the uncoupled signal from the through port, and output the reflected signal (for example, signal A) from the isolation port. The reflected signal may include: the signal reflected from the coupling port and the signal reflected from the through port.

[0115] It is understandable that, when a reactance unit is provided at the coupled port, the reactance unit can reflect part or all of the coupled signal to the isolated port. When a reactance unit is provided at the through port, the reactance unit can reflect part or all of the uncoupled signal to the isolated port.

[0116] Therefore, the phase of the reflected signal output at the isolated port is related to both the reactance at the coupled port and the reactance at the through port. Specifically, when the reactance at the coupled port changes, the phase of the reflected signal output at the isolated port changes; or, when the reactance at the through port changes, the phase of the reflected signal output at the isolated port changes.

[0117] In the embodiment of the present application, by changing the reactance at the through port 5c and / or the reactance at the coupling port 5b, the phase of the signal A output from the isolation port in the coupling unit 402 can be changed.

[0118] In the embodiment of the present application, the power of the signal output by the through port and the coupled port of the coupling unit 402 may be the same or different. The coupling unit 402 may be a coupler or any other device with the same function, which is not specifically limited here.

[0119] Exemplarily, the coupling unit 402 may be a 3dB coupler. The power of the signal outputted by the through port and the coupled port of the 3dB coupler is the same.

[0120] The power amplification unit 403 is used to amplify the signal A. The power amplification unit 403 may include one or more power amplification units, which are not specifically limited here.

[0121] In some embodiments, the power amplifier unit 403 operates in a class B or class C mode. When the power of signal A is relatively low, the power amplifier unit 403 is not turned on; when the power of signal A is relatively high, the transistor in the power amplifier unit 403 is turned on, and the power amplifier unit 403 amplifies signal A.

[0122] The reactance unit 404 is used to adjust the reactance of the through port 5 c so that the phase shift of the signal A transmitted through the coupling unit 402 is changed, and thus the phase of the signal A is changed.

[0123] The reactance unit 404 may include one or more reactance elements, such as capacitors, inductors, or magnetic beads, etc. No specific limitation is given here. In some embodiments, the reactance unit 404 includes: a capacitor. The capacitor is easy to disassemble and replace, which is convenient for debugging the power amplifier circuit.

[0124] The reactance unit 405 is used to adjust the reactance of the coupling port 5 b so that the phase shift of the signal A transmitted through the coupling unit 402 is changed, and thus the phase of the signal A is changed.

[0125] The reactance unit 405 may include one or more reactance elements, such as capacitors, inductors, or magnetic beads, etc., which are not specifically limited here.

[0126] In some embodiments, the reactance of the reactance unit 405 and the reactance of the reactance unit 404 are less than or equal to the threshold value A. The threshold value A can be 0.1, 0.5 or any value, which is not specifically limited here. In this way, the difference between the phase of the signal reflected from the coupling port to the isolation port and the phase of the signal reflected from the through port to the isolation port can be reduced, and the insertion loss of the coupling unit 402 can be reduced.

[0127] Exemplarily, the reactance unit 405 includes: a capacitor C3, and the difference between the capacitance value of the capacitor C3 and the capacitance value of the capacitor C2 is less than a threshold value A. The threshold value A may be 0.1 pf, 0.5 pf or any value, which is not specifically limited here.

[0128] In this way, the capacitance value of the capacitor C3 is close to or even the same as the capacitance value of the capacitor C2 , so that the reactance of the reactance unit 405 is close to or even the same as the reactance of the reactance unit 404 , thereby reducing the insertion loss of the coupling unit 402 .

[0129] In some embodiments, the coupling unit 402 is a 3dB coupler, so that the insertion loss of the coupling unit 402 can be reduced.

[0130] It is understandable that both the reactance unit 404 and the reactance unit 405 can adjust the phase of the signal A, so the power amplifier circuit may include any one of the reactance unit 404 and the reactance unit 405, or may include the reactance unit 404 and the reactance unit 405. No specific limitation is made here.

[0131] The coupling unit 406 is used to decompose the signal B into a signal b1 and a signal b2 at the input port 6a, and output the signal b1 from the coupling port 6b and output the signal b2 from the through port 6c. The signal b1 output by the coupling unit 406 is orthogonal to the signal b2 output by the coupling unit 406.

[0132] Orthogonality can be understood as a phase difference of 90 degrees between two signals. In the embodiment of the present application, orthogonality can be understood as a phase difference of 90 degrees between the signal b1 output from the coupling port 6b and the signal b2 output from the through port 6c; or it can be understood as a difference of 90 degrees between the phase shift of the signal b1 at the coupling unit 406 and the phase shift of the signal b2 at the coupling unit 406 (the difference between the phase of the signal b2 at the through port and the phase at the input port). The phase shift of the signal b1 at the coupling unit 406 is the difference between the phase shift of the signal b1 at the coupling port 6b and the phase at the input port 6a; the phase shift of the signal b2 at the coupling unit 406 is the difference between the phase of the signal b2 at the through port 6c and the phase at the input port 6a.

[0133] It should be understood that the orthogonality in the embodiment of the present application can be standard orthogonality in a mathematical sense (for example, the phase difference between the signal b1 and the signal b2 output by the coupling unit 406 is 90 degrees), or can be orthogonality within a certain error range. Taking the error range of plus or minus 1 degree as an example, when the phase difference between the signal b1 and the signal b2 output by the coupling unit 406 is between 89 degrees and 91 degrees, the signal b1 and the signal b2 are orthogonal.

[0134] The coupling unit 406 may be a coupler, or any other device having the same function, which is not specifically limited here.

[0135] The power amplifying unit 407 is used to amplify the signal b1; the power amplifying unit 407 is used to amplify the signal b2.

[0136] In some embodiments, the power amplification unit 407 may include one or more power amplifiers; the power amplification unit 408 may include one or more power amplifiers, which are not specifically limited here.

[0137] In some embodiments, both power amplifier unit 407 and power amplifier unit 408 operate in class AB mode, the transistor in power amplifier unit 407 is in the on state, and power amplifier unit 407 amplifies signal b1; the transistor in power amplifier unit 408 is in the on state, and power amplifier unit 408 amplifies signal b2.

[0138] The coupling unit 409 is used to combine the amplified signal b1 and the amplified signal b2 to obtain an amplified RF signal. The phase of the amplified signal b1 is affected by the impedance between the power amplification unit 407 and the coupling unit 409. The impedance is affected by the phase and amplitude of the amplified signal A transmitted by the isolation port 7d.

[0139] The coupling unit 409 may be a coupler, or any other device having the same function, which is not specifically limited here.

[0140] Below Figure 5 The working principle and efficiency of the power amplifier circuit shown are described. Taking the case where the power amplifier unit 403 works in the class B mode and the power amplifier unit 407 and the power amplifier unit 408 both work in the class AB mode as an example, the working principle is as follows:

[0141] When the input power of the RF signal is small, the power of the signal A is insufficient to turn on the transistor in the power amplifier unit 403, the isolation port 7d of the coupling unit 409 is open, and the control signal unit does not perform load modulation on the signal amplifier unit.

[0142] At this time, the power amplifier unit 407 and the power amplifier unit 408 amplify the signal b1 and the signal b2 respectively. Since the power of the signal b1 and the signal b2 is low, and the power amplifier unit 407 and the power amplifier unit 408 both work in the linear region, the efficiency of the power amplifier unit 407 and the power amplifier unit 408 is low, and the efficiency of the power amplifier circuit is low.

[0143] As the input power gradually increases, the power of signal A and the power of signal B gradually increase, the efficiency of power amplification unit 407 and power amplification unit 408 gradually increases, and the efficiency of the power amplifier circuit gradually increases.

[0144] When the input power of the RF signal reaches power A, the power of signal A triggers the power amplifier unit 403 to start working, and the amplified signal A is transmitted to the isolation port 7d of the coupling unit 409. The amplified signal A, the amplified signal b1 and the amplified signal b2 are superimposed, so that the output power of the power amplifier circuit is increased.

[0145] In addition, when the input power of the RF signal reaches power A, the control signal unit starts to load modulate the signal amplification unit. It can also be understood that the amplified signal A starts to modulate the impedance at the through port 7c of the coupling unit 409 and the impedance at the coupling port 7b of the coupling unit 409.

[0146] As the input power of the RF signal increases, the power of the amplified signal A gradually increases, so that the load impedance of the power amplifier unit 407 and the load impedance of the power amplifier unit 408 gradually decrease, and thus the efficiency of the power amplifier unit 407 and the efficiency of the power amplifier unit 408 can still be maintained at a high level, and the overall power amplification efficiency of the power amplifier circuit can still be maintained at a high level.

[0147] When the input power of the RF signal reaches power B, the power amplifier unit 403, the power amplifier unit 407 and the power amplifier unit 408 are all saturated, and the power of the amplified RF signal (also referred to as the output power of the power amplifier circuit) reaches the maximum. In addition, the load impedance of the power amplifier unit 407 and the power amplifier unit 408 is optimally matched with the source impedance, and the efficiency of the power amplifier circuit reaches the maximum.

[0148] It can be understood that the load impedance of the signal amplification unit in the power amplifier circuit provided in the embodiment of the present application is related to the amplitude and phase of the signal transmitted by the control signal unit. The amplitude and phase of the signal are related to the phase shift and insertion loss of the coupling unit 402. Therefore, Figure 5 The difficulty of debugging the power amplifier circuit shown is related to the phase shift variation and insertion loss variation of the coupling unit 402 .

[0149] Combine the following Figure 6The phase shift change and insertion loss change of the coupling unit 402 are described.

[0150] For example, Figure 6 A schematic diagram of a phase shift of a signal A in a coupling unit 402 and a change in insertion loss of the coupling unit 402 when a capacitance C2 changes provided in an embodiment of the present application.

[0151] like Figure 6 As shown, in the scenario where the capacitance C2 is 1.5 pF, the phase shift of the signal A in the coupling unit 402 can be as follows: Figure 6 As shown in curve 501 in a of FIG. 1 ; in the scenario where the capacitance C2 is 2 pF, the phase shift of the signal A in the coupling unit 402 can be as follows Figure 6 As shown in curve 502 in a of FIG. 1 ; in the scenario where the capacitance C2 is 1.5 pF, the insertion loss of the signal A in the coupling unit 402 can be as follows Figure 6 As shown in curve 503 in b; in the scenario where the capacitance C2 is 2pF, the insertion loss of the signal A in the coupling unit 402 can be as follows Figure 6 As shown in curve 504 in b.

[0152] from Figure 6 It can be seen from FIG. 4 that if the capacitance value is adjusted from 1.5 pf to 2 pf, the phase shift of the signal A in the coupling unit 402 changes between 10 degrees and 15 degrees, and the insertion loss of the coupling unit 402 changes between 0.002 dB and 0.006 dB.

[0153] Compared to Figure 3 The LMBA shown, Figure 5 In the process of adjusting the phase of the signal A, the insertion loss of the coupling unit 402 changes slightly, so that the amplitude of the amplified signal A changes slightly, and thus the change of the load impedance of the signal amplification unit is easy to predict, and the design difficulty of the power amplifier circuit is small. In addition, the insertion loss of the coupling unit 402 is small, and the power loss is small.

[0154] In the above Figure 5 On the basis of the embodiment shown, the power amplifier circuit provided in the embodiment of the present application further includes: a phase compensation unit. The phase compensation unit is located on the signal amplification unit. For example, between the power divider 401 and the coupling unit 402. The phase compensation unit is used to compensate for the difference in phase adjustment of the coupling unit 402 for signals of different frequencies, so that when the power amplifier circuit amplifies signals of different frequencies, the phase difference between the signal transmitted by the control signal unit and the signal transmitted by the signal amplification unit is maintained within a preset range. In this way, broadband phase shifting of the power amplifier circuit can be achieved.

[0155] For example, Figure 7As shown, one end of the phase compensation unit 601 is connected to the port 4 c of the power divider 401 , and the other end of the phase compensation unit 601 is connected to the input port 6 a of the coupling unit 406 .

[0156] The phase compensation unit 601 is used to adjust the phase of the signal B so that the difference between the phase shift of the signal B and the difference A is less than or equal to the preset value A, and the difference A is the difference between the phase shift of the signal A in the coupling unit 402 and the phase shift of the signal A of the preset frequency in the coupling unit 402. The preset value A can be 1 degree, 5 degrees or any value, which is not specifically limited here.

[0157] In this way, the phase of signal B can be adjusted through the phase compensation unit 601 to compensate for the phase shift difference of signal A of different frequencies in the coupling unit 402, so that the power amplifier circuit can support signal amplification of multiple frequencies, thereby improving the applicability of the power amplifier circuit and improving practicality.

[0158] In some embodiments, the phase compensation unit 601 can achieve a fixed degree of phase shift on the radio frequency signal at the center frequency, and the phase shift angle will change linearly at other frequencies.

[0159] The fixed degree can be 90 degrees, 85 degrees or any value, which is not specifically limited here. In this way, it can be similar to the phase shift change law of the coupling unit 402 on the RF signal, so that the phase difference between signal A and signal B at each frequency is close to the phase difference between signal A and signal B at the center frequency.

[0160] In the embodiment of the present application, the phase compensation unit 601 may be a microstrip line (eg Figure 8 (as shown in a in the figure).

[0161] The phase compensation unit 601 may also be a phase shift unit with a series inductor π-type network structure. Figure 8 As shown in b, the phase shift unit of the series inductor π-type network structure includes: a capacitor C11, a capacitor C12, and an inductor L11. The first end of the inductor L11 is electrically connected to the first end of the capacitor C11 and serves as the input end of the series inductor π-type network, the second end of the capacitor C11 is grounded, the second end of the inductor L11 is electrically connected to the first end of the capacitor C12 and serves as the output end of the series inductor π-type network, and the second end of the capacitor C12 is grounded.

[0162] The phase compensation unit 601 can also be a phase shift unit with a series capacitor π-type network structure. Figure 8 For example, Figure 8As shown in c, the phase shift unit of the series capacitor π-type network structure includes: capacitor C11, inductor L11, and inductor L12. The first end of the capacitor C11 is electrically connected to the first end of the inductor L11 and serves as the input end of the series capacitor π-type network, the second end of the inductor L11 is grounded, the second end of the capacitor C11 is electrically connected to the first end of the inductor L12 and serves as the output end of the series capacitor π-type network, and the second end of the inductor L12 is grounded.

[0163] The phase compensation unit 601 may also be a phase shift unit with a T-type network structure of series inductors. Figure 8 As shown in d, the phase shift unit of the series inductor T-type network structure includes: a capacitor C11, an inductor L11, and an inductor L12. The first end of the inductor L11 serves as an input end of the series inductor T-type network, the second end of the inductor L11, the first end of the inductor L12, and the first end of the capacitor C11 are electrically connected, the second end of the capacitor C11 is grounded, and the second end of the inductor L12 serves as an output end of the series inductor T-type network.

[0164] The phase compensation unit 601 may also be a phase shift unit with a T-type network structure of series capacitors. Figure 8 As shown in FIG. 5 , the phase shift unit of the series capacitor T-type network structure includes: a capacitor C11, a capacitor C12, and an inductor L11. The first end of the capacitor C11 serves as the input end of the series capacitor T-type network, the second end of the capacitor C11, the first end of the capacitor C12, and the first end of the inductor L11 are electrically connected, the second end of the inductor L11 is grounded, and the second end of the capacitor C12 serves as the output end of the series capacitor T-type network.

[0165] The above structures are only examples, and the phase compensation unit 601 may also be any type of structure (phase shifting unit) with a phase adjustment function, which is not specifically limited here.

[0166] For example, taking the RF signal as an N77 signal with a frequency range of 3.3 GHz to 4.2 GHz, and the capacitance values ​​of the capacitor C2 as 1.5 pF, 2 pF, and 2.5 pF, Fig. 9 A schematic diagram of a change in the difference between the phase of a signal A output by a coupling unit 402 and the phase of a signal B input to a coupler 406 provided in an embodiment of the present application.

[0167] like Fig. 9 As shown, after adding the phase compensation unit, in the scenario where the capacitor C2 is 1.5 pF, the difference between the phase of the signal A output by the coupling unit 402 and the phase of the signal B input to the coupler 406 can be as follows: Fig. 9After adding the phase compensation unit, in the scenario where the capacitor C2 is 1.5 pF, the phase of the signal A output by the coupling unit 402 and the phase difference between the signal B input to the coupler 406 can be as follows Fig. 9 After adding the phase compensation unit, in the scenario where the capacitor C2 is 1.5 pF, the phase of the signal A output by the coupling unit 402 and the phase difference between the signal B input to the coupler 406 can be as follows Fig. 9 As shown by the curve 803 in Fig. 9 It can be seen that when the capacitance C1 is 1.5pF, the phase difference between signal A and signal B is between 100 degrees and 105 degrees under RF signals of different frequencies. When the capacitance C1 is 2pF, the phase difference between signal A and signal B is between 90 degrees and 100 degrees. When the capacitance C1 is 2.5pF, the phase difference between signal A and signal B is between 80 degrees and 85 degrees.

[0168] from Fig. 9 It can be seen that the phase difference between signal A and signal B at each frequency is close to the phase difference between signal A and signal B at the center frequency, which can realize broadband phase shifting of the power amplifier circuit.

[0169] In some embodiments, the phase compensation unit may further include two phase compensation modules, one phase compensation module is arranged between the coupling unit 406 and the power amplification unit 407, and the other phase compensation module is arranged between the coupling unit 406 and the power amplification unit 408. In this way, the phase of the signal b1 and the phase of the signal b2 can be adjusted, so that the phase difference between the signal transmitted by the control signal unit and the signal transmitted by the signal amplification unit is maintained within a preset range.

[0170] The structure of the phase compensation module is similar to that of the above-mentioned phase compensation unit 601 and will not be described in detail here.

[0171] It is understandable that the above embodiment takes the control signal unit including: coupling unit 402 and power amplification unit 403; the signal amplification unit including: coupling unit 406, power amplification unit 407, power amplification unit 408 and coupling unit 409 as an example to illustrate the power amplifier circuit of the load modulation structure. It is understandable that in addition to the above power amplification unit, the control signal unit may also include other functional units, such as a voltage stabilizing unit for stabilizing the voltage, a current limiting unit for limiting the current in the control signal unit to be less than a certain fixed value, etc.; the signal amplification unit may also include other functional units, such as a voltage stabilizing unit for stabilizing the voltage, a current limiting unit for limiting the current in the signal amplification unit to be less than a certain fixed value, etc.; no specific limitation is made here.

[0172] In addition, the power amplifier circuit of the load modulation structure may also be any other structure, for example, the signal amplification unit may include more or fewer power amplification units. The structure of the power amplifier circuit of the load modulation structure is not specifically limited here.

[0173] Above Figures 5 to 9 In the embodiment shown, the power amplifier circuit divides the radio frequency signal into two signals through a power divider. Figures 10 to 14 A power amplifier circuit for dividing a radio frequency signal into two signals through a coupler is described.

[0174] For example, Fig.10 This is a schematic diagram of the structure of another power amplifier circuit provided in an embodiment of the present application. Fig.10 As shown, the power amplifier includes: a coupling unit 902, a power amplifying unit 903, a reactance unit 904, a coupling unit 905, a power amplifying unit 906, a power amplifying unit 907 and a coupling unit 908. The control signal unit may include: a coupling unit 902, a power amplifying unit 903 and a reactance unit 904; the signal amplifying unit may include: a coupling unit 902, a coupling unit 905, a power amplifying unit 906, a power amplifying unit 907 and a coupling unit 908.

[0175] The coupling unit 902 includes: an input port 8a, a coupling port 8b, a through port 8c and an isolated port 8d; the coupling unit 905 includes: an input port 9a, a coupling port 9b, a through port 9c and an isolated port 9d; the coupling unit 908 includes: an input port 10a, a coupling port 10b, a through port 10c and an isolated port 10d.

[0176] like Fig. 9 As shown, the input port 8a of the coupling unit 902 is used to input the radio frequency signal; the isolation port 8d of the coupling unit 902 is connected to the input end of the power amplifier unit 903, and the output end of the power amplifier unit 903 is connected to the isolation port 10d of the coupling unit 908; the through port 8c of the coupling unit 902 is connected to one end of the reactance unit 904, and the other end of the reactance unit 904 is grounded.

[0177] The coupling port 8b of the coupling unit 902 is connected to the input port 9a of the coupling unit 905; the coupling port 9b of the coupling unit 905 is connected to the input end of the power amplifier unit 906, and the output end of the power amplifier unit 906 is connected to the through port 10c of the coupling unit 908; the through port 9c of the coupling unit 905 is connected to the input end of the power amplifier unit 907, and the output end of the power amplifier unit 907 is connected to the isolation port 10d of the coupling unit 908; the input port 10a of the coupling unit 908 is used to output the amplified RF signal, and the isolation port 9d of the coupling unit 905 is grounded.

[0178] In the embodiment of the present application, the coupling unit 902 is used to divide the radio frequency signal into two paths, namely signal A and signal B. The power of signal A and signal B may be the same or different, which is not specifically limited here.

[0179] The coupling unit 902 is further configured to adjust the phase of the signal A under the control of the reactance unit 904 . The difference between the phase of the signal A and the phase of the RF signal is related to the reactance of the reactance unit 404 .

[0180] The power amplification unit 903 is used to amplify the power of the signal A.

[0181] The reactance unit 904 is used to adjust the reactance of the through port 5 c so that the difference between the phase of the signal A and the phase of the radio frequency signal changes, and the phase of the signal A changes.

[0182] The structure of the reactance unit 904 may refer to the structure of the reactance unit 404 described above, and will not be described in detail here.

[0183] The coupling unit 905 is used to decompose the signal B into a signal b1 and a signal b2. The signal b1 and the signal b2 are orthogonal. Orthogonal can be understood as a phase difference of 90 degrees between the signal b1 and the signal b2.

[0184] The power amplification unit 906 is used to amplify the signal b1; the power amplifier 306 is used to amplify the signal b2.

[0185] The coupling unit 908 is used to combine the amplified signal b1 and the amplified signal b2 to obtain an amplified RF signal. The phase of the amplified signal b1 is affected by the impedance between the power amplifier unit 906 and the coupling unit 908. The impedance is affected by the phase and amplitude of the amplified signal A transmitted by the isolation port 10d.

[0186] The structures and functions of the power amplification unit 903, the coupling unit 905, the power amplification unit 906, the power amplification unit 907 and the coupling unit 908 can refer to the above Figure 5 The relevant descriptions of the corresponding devices in will not be repeated in detail here.

[0187] Below Fig.10 The working principle and efficiency of the power amplifier circuit shown are explained. The working principle is as follows:

[0188] When the input power of the RF signal is small, the power of the signal A output by the coupling unit 402 is insufficient to turn on the transistor in the power amplification unit 903, the isolation port 10d of the coupling unit 908 is open, and the control signal unit does not perform load modulation on the signal amplification unit.

[0189] At this time, the power amplifier unit 906 and the power amplifier unit 907 amplify the signal b1 and the signal b2 respectively. Since the power of the signal b1 and the signal b2 is relatively low, and the power amplifier unit 906 and the power amplifier unit 907 both operate in the linear region, the efficiency of the power amplifier unit 906 and the power amplifier unit 907 is relatively low, and the efficiency of the power amplifier circuit is relatively low.

[0190] As the input power gradually increases, the power of signal A and the power of signal B gradually increase, the efficiency of power amplification unit 906 and power amplification unit 907 gradually increases, and the efficiency of the power amplifier circuit gradually increases.

[0191] When the power of the RF signal reaches power A, the power of signal A triggers the power amplifier unit 903 to start working, and the amplified signal A is transmitted to the isolation port 10d of the coupling unit 908. The amplified signal A, the amplified signal b1 and the amplified signal b2 are superimposed, so that the output power of the power amplifier circuit is increased.

[0192] In addition, when the input power of the RF signal reaches power A, the control signal unit starts to load modulate the signal amplification unit. It can also be understood that the amplified signal A starts to modulate the impedance of the through port 10c of the coupling unit 908 and the impedance at the coupling port 7b of the coupling unit 908. As the input power of the RF signal increases, the power of the amplified signal A gradually increases, so that the load impedance of the power amplification unit 906 and the load impedance of the power amplification unit 907 gradually decrease, and then the efficiency of the power amplification unit 407 and the efficiency of the power amplification unit 408 can still be maintained at a high level, and the efficiency of the power amplification of the power amplifier circuit as a whole can still be maintained at a high level.

[0193] When the input power of the RF signal reaches power B, the power amplifier unit 903, the power amplifier unit 906 and the power amplifier unit 907 are all saturated, and the output power of the power amplifier circuit reaches the maximum. In addition, the load impedance of the power amplifier unit 906 and the power amplifier unit 907 is optimally matched with the source impedance, and the efficiency of the power amplifier circuit reaches the maximum.

[0194] It can be understood that the load impedance of the signal amplification unit in the power amplifier circuit provided in the embodiment of the present application is related to the amplitude and phase of the signal transmitted by the control signal unit. The amplitude and phase of the signal are related to the phase shift and insertion loss of the coupling unit 902. Therefore, Fig.10 The difficulty of debugging the power amplifier circuit shown is related to the phase shift change and insertion loss change of the coupling unit 902 .

[0195] Combine the following Fig.11 The phase shift change and insertion loss change of each signal in the coupling unit 902 are described.

[0196] For example, taking the RF signal as an N77 signal with a frequency range of 3.3 GHz to 4.2 GHz, and the capacitance value of the capacitor C4 as 1.5 pF, 1.8 pF, and 2.2 pF, Fig.11 A schematic diagram of a phase shift of a signal A in a coupling unit 902 and a transmission loss change of the signal A in the coupling unit 902 when a capacitance C4 changes provided in an embodiment of the present application.

[0197] like Fig.11 As shown, in the scenario where the capacitor C4 is 1.5 pF, the phase shift change of the signal A in the coupling unit 902 can be as follows: Fig.11 As shown in curve 1001 in a of FIG. 1 ; in the scenario where the capacitor C4 is 1.8 pF, the phase shift change of the signal A in the coupling unit 902 can be as follows Fig.11 As shown in the curve 1002 in a of FIG. 1 ; in the scenario where the capacitor C4 is 2.2 pF, the phase shift change of the signal A transmitted in the coupling unit 902 can be as follows Fig.11 As shown by the curve 1003 in a;

[0198] In the scenario where the capacitance C4 is 1.5 pF, the loss variation of the signal A transmitted in the coupling unit 902 can be as follows: Fig.11 As shown in curve 1004 in b in FIG. 1 ; in the scenario where the capacitance C4 is 1.8 pF, the loss variation of the signal A transmitted in the coupling unit 902 can be as follows Fig.11 As shown in curve 1005 in b of FIG. In the scenario where the capacitance C4 is 2.2 pF, the loss variation of the signal A transmitted in the coupling unit 902 can be as follows: Fig.11 As shown in curve 1006 in b.

[0199] from Fig.11 It can be seen that if the capacitance value is adjusted from 1.5pF to 1.8pF, the phase shift of signal A transmitted in coupling unit 902 changes between 5 degrees and 15 degrees, and the loss of signal A transmitted in coupling unit 902 changes between 0dB and 0.02dB, which is a small change. If the capacitance value is adjusted from 1.8pF to 2.2pF, the phase shift of signal A transmitted in coupling unit 902 changes between 5 degrees and 15 degrees, and the loss of signal A transmitted in coupling unit 902 changes between 0dB and 0.03dB, which is a small change.

[0200] In addition, when C4 has the same capacitance value, the phase shifts of signals A of different frequencies in the coupling unit 902 are different. When C4 has the same capacitance value, the losses of signals A of different frequencies transmitted in the coupling unit 902 vary differently.

[0201] Therefore, before and after the capacitance value of the capacitor C4 is adjusted, the transmission loss of the signal A in the coupling unit 902 does not change much.

[0202] also, Fig.10The power amplifier circuit shown does not require a power divider, and the signal is decomposed into two signals through a coupling unit. The size is small, which is conducive to the miniaturization of the device.

[0203] It should be noted that the size of the coupling unit is inversely proportional to the characteristic impedance of the coupling unit. The size of the power divider is inversely proportional to the characteristic impedance of the power divider. Under the same characteristic impedance, since the coupling unit can be a multi-layer structure, the projection area of ​​the coupling unit on the circuit is smaller than that of the power divider, and thus the power divider circuit occupies a smaller area on the printed circuit board, which is conducive to the miniaturization of electronic equipment.

[0204] Compared to Figure 3 As shown in LMBA, Fig.10 In the process of adjusting the phase of signal A in the power amplifier circuit shown, the insertion loss of the coupling unit 902 changes slightly, so that the amplitude of the amplified signal A changes slightly, and the phase control of signal A and the amplitude control of signal A can be decoupled. In this way, when performing phase control of signal A, there is no need to consider the impact on the amplitude of signal A, the change of the load impedance of the signal amplification unit is easy to predict, and the design difficulty of the power amplifier circuit is reduced. In addition, the insertion loss of the coupling unit 902 is small, and the power loss is small.

[0205] For example, Fig.12 Schematic diagram of phase shift and insertion loss of signal B in coupling unit 902 provided in an embodiment of the present application. Fig.12 As shown, in the scenario where the capacitor C4 is 1.5 pF, the phase shift change of the signal B in the coupling unit 902 can be as follows: Fig.12 As shown in curve 1201 in a of FIG. 1 ; in the scenario where the capacitor C4 is 1.8 pF, the phase shift change of the signal B in the coupling unit 902 can be as follows Fig.12 As shown in curve 1202 in a of FIG. 1 ; in the scenario where the capacitor C4 is 2.2 pF, the phase shift change of the signal B in the coupling unit 902 can be as follows Fig.12 As shown by the curve 1203 in a;

[0206] In the scenario where the capacitance C4 is 1.5 pF, the loss variation of the signal B transmitted in the coupling unit 902 can be as follows: Fig.12 As shown in curve 1204 in b in FIG. 1 ; in the scenario where the capacitance C4 is 1.8 pF, the loss variation of the signal B transmitted in the coupling unit 902 can be as follows Fig.12 In the scenario where the capacitance C4 is 2.2 pF, the loss of the signal B transmitted in the coupling unit 902 may be changed as follows: Fig.12 As shown in curve 1206 in b.

[0207] from Fig.12It can be seen that when the capacitance value of capacitor C4 is adjusted from 1.5pF to 1.8pF, the phase shift of signal B changes between 0 and 2 degrees, and the loss of signal B transmitted in coupling unit 902 changes between 0.03dB and 0.05dB, which is a small change. When the capacitance value is adjusted from 1.8pF to 2.2pF, the phase shift of signal B changes between 0 and 2 degrees, and the loss of signal B transmitted in coupling unit 902 changes between 0.03dB and 0.05dB, which is a small change.

[0208] In addition, when the capacitor C4 has the same capacitance value, the phase shifts of signals B of different frequencies in the coupling unit 902 are different. When the capacitor C4 has the same capacitance value, the losses of signals B of different frequencies transmitted in the coupling unit 902 vary differently.

[0209] In the above Fig.10 On the basis of the embodiment shown, the power amplifier circuit provided in the embodiment of the present application further includes: a phase compensation unit. The phase compensation unit is located between 8b and the input port 9a of the coupling unit 905. The phase compensation unit is used to compensate for the difference in phase adjustment of the coupling unit 902 to signals of different frequencies, so that when the power amplifier circuit amplifies signals of different frequencies, the phase difference between the signal transmitted by the control signal unit and the signal transmitted by the signal amplification unit is maintained within a preset range. In this way, broadband phase shifting of the power amplifier circuit can be achieved.

[0210] For example, Fig.13 As shown, one end of the phase compensation unit 1101 is connected to the coupling port 8 b of the coupling unit 902 , and the other end of the phase compensation unit 1101 is connected to the input port 9 a of the coupling unit 905 .

[0211] The phase compensation unit 1101 is used to adjust the phase of the signal B.

[0212] In some embodiments, the phase compensation unit 1101 can make the difference between the phase shift of signal B and the difference B less than or equal to the preset value B, where the difference B is the difference between the phase shift of signal A in the coupling unit 902 and the phase shift of signal A of a preset frequency in the coupling unit 902. The phase shift of signal A in the coupling unit 902 can be understood as the phase of signal A output by the coupling unit 902 and the phase of the RF signal input to the coupling unit 902; the phase shift of signal A of a preset frequency in the coupling unit 902 can be understood as the phase of signal A of a preset frequency output by the coupling unit 902 and the phase of the RF signal of the preset frequency input to the coupling unit 902.

[0213] The preset value B may be 1 degree, 5 degrees or any other value, and is not specifically limited here.

[0214] In this way, the phase of signal B can be adjusted through the phase compensation unit 1101 to compensate for the phase shift difference of signal A of different frequencies in the coupling unit 902, so that the power amplifier circuit can support signal amplification of multiple frequencies, thereby improving the application range of the power amplifier circuit and improving practicality.

[0215] In some other embodiments, the phase compensation unit 1101 can make the difference between the phase shift of the signal B and the difference C less than or equal to the preset value B. The difference C is the difference between the difference B and the difference D, and the difference D is the difference between the phase shift of the signal B in the coupling unit 902 and the phase shift of the signal B of the preset frequency in the coupling unit 902.

[0216] The phase shift of signal B in the coupling unit 902 can be understood as the difference between the phase of signal B output by the coupling unit 902 and the phase of the RF signal input to the coupling unit 902; the phase shift of signal B of the preset frequency in the coupling unit 902 can be understood as the difference between the phase of signal B of the preset frequency output by the coupling unit 902 and the phase of the RF signal of the preset frequency input to the coupling unit 902.

[0217] It is understandable that at different frequencies, the phase difference between the input port and the coupling port of the coupling unit 902 will also be different. Therefore, the phase shift of the signal B by the phase compensation unit is also related to the phase shift of the signal B in the coupling unit 902.

[0218] Above Figures 10 to 13 In the illustrated embodiment, the through port 8 c of the coupling unit 902 is connected to the reactance unit 904 ; and the coupling port 8 b of the coupling unit 902 is connected to the coupling unit 905 .

[0219] In some embodiments, the through port 8c of the coupling unit 902 may also be connected to the coupling unit 905; and the coupling port 8b of the coupling unit 902 is connected to the reactance unit 904. No specific limitation is given here.

[0220] In the embodiments of the present application, the communication device can be understood as a device with a communication function. The device includes: a power amplifier circuit provided in the embodiments of the present application to realize a signal amplification function. The communication device can include the above-mentioned electronic equipment, base stations, radars, etc. No specific limitation is made here.

[0221] For example, Fig.14 This is a schematic diagram of the structure of an electronic device provided in an embodiment of the present application. Fig.14As shown, the electronic device includes: a processor 110, an external memory interface 120, an internal memory 121, a universal serial bus (USB) interface 130, a charging management module 140, a power management module 141, a battery 142, an antenna 1, an antenna 2, a mobile communication module 150, a wireless communication module 160, an audio module 170, a speaker 170A, a receiver 170B, a microphone 170C, an earphone interface 170D, a sensor module 180, a button 190, a motor 191, an indicator 192, a camera 193, a display screen 194, and a subscriber identification module (SIM) card interface 195, etc. Among them, the sensor module 180 may include a pressure sensor 180A, a gyroscope sensor 180B, an air pressure sensor 180C, a magnetic sensor 180D, an acceleration sensor 180E, a distance sensor 180F, a proximity light sensor 180G, a fingerprint sensor 180H, a temperature sensor 180J, a touch sensor 180K, an ambient light sensor 180L, a bone conduction sensor 180M, etc.

[0222] It is to be understood that the structure illustrated in the embodiments of the present application does not constitute a specific limitation on the electronic device. In other embodiments of the present application, the electronic device may include more or fewer components than shown in the figure, or combine certain components, or split certain components, or arrange the components differently. The components shown in the figure may be implemented in hardware, software, or a combination of software and hardware.

[0223] The wireless communication function of the electronic device can be implemented through the antenna 1, the antenna 2, the mobile communication module 150, the wireless communication module 160, the modulation and demodulation processor, etc.

[0224] Antenna 1 and antenna 2 are used to transmit and receive electromagnetic wave signals. Each antenna in the electronic device can be used to cover a single or multiple communication frequency bands. Different antennas can also be reused to improve the utilization of the antennas. For example, antenna 1 can be reused as a diversity antenna for a wireless local area network. In some other embodiments, the antenna can be used in combination with a tuning switch.

[0225] The mobile communication module 150 can provide solutions for wireless communications including 2G / 3G / 4G / 5G, etc., applied in electronic devices. The wireless communication module 160 can provide solutions for wireless communications including wireless local area networks (WLAN) (such as wireless fidelity (Wi-Fi) networks), Bluetooth (BT), global navigation satellite system (GNSS), frequency modulation (FM), near field communication (NFC), infrared (IR), etc., applied in electronic devices. In some embodiments, the antenna 1 of the electronic device is coupled to the mobile communication module 150, and the antenna 2 is coupled to the wireless communication module 160, so that the electronic device can communicate with the network and other devices through wireless communication technology.

[0226] For example, Fig.15 As shown in a in FIG. 1 , the mobile communication module 150 may include: a baseband chip 31 , a radio frequency integrated circuit (RFIC) 32 and a power amplifier circuit 33 .

[0227] The baseband chip 31 is used to convert the data from the processor 110 into a baseband signal, including modulation and demodulation, digital filtering, equalization processing, etc. of the baseband signal. The RFIC 32 is used to convert the baseband signal from the baseband chip 31 into a radio frequency signal, which is transmitted through the power amplifier circuit 33 and the antenna 34. It should be noted that the baseband chip 31 and the RFIC 32 can also be integrated with the processor 110 in the SoC.

[0228] The power amplifier circuit 33 provided in the embodiment of the present application can improve the efficiency of power amplification during power fallback. Figures 5 to 13 shown.

[0229] For example, Fig.15 As shown in b, the wireless communication module 160 may include: a baseband chip 41, a radio frequency integrated circuit (RFIC) 42 and a power amplifier circuit 43.

[0230] The baseband chip 41 is used to convert the data from the processor 110 into a baseband signal, including modulation and demodulation, digital filtering, equalization processing, etc. of the baseband signal. The RFIC 42 is used to convert the baseband signal from the baseband chip 41 into a radio frequency signal, which is transmitted through the power amplifier circuit 43 and the antenna 44. It should be noted that the baseband chip 41 and the RFIC 42 can also be integrated with the processor 110 in the SoC.

[0231] The power amplifier circuit 43 provided in the embodiment of the present application can improve the efficiency of power amplification during power fallback. Figures 5 to 13 shown.

[0232] It should be noted that the module names involved in the embodiments of the present application can be defined as other names as long as the functions of each module can be achieved, and there is no specific restriction on the names of the modules.

[0233] It should be noted that the user information (including but not limited to user device information, user personal information, etc.) and data (including but not limited to data used for analysis, stored data, displayed data, etc.) involved in the embodiments of the present application are all information and data authorized by the user or fully authorized by all parties, and the collection, use and processing of relevant data must comply with the relevant laws, regulations and standards of the relevant countries and regions, and provide corresponding operation entrances for users to choose to authorize or refuse.

[0234] The above specific implementation methods further illustrate the purpose, technical solutions and beneficial effects of the present invention in detail. It should be understood that the above are only specific implementation methods of the present invention and are not intended to limit the scope of protection of the present invention. Any modifications, equivalent substitutions, improvements, etc. made on the basis of the technical solutions of the present invention should be included in the scope of protection of the present invention.

Claims

1. A power amplifier circuit, characterized in that: include: A power divider, a first coupling unit, a first reactance unit, a first power amplification unit and a signal amplification unit; The power divider includes: a first port, a second port and a third port; the first coupling unit includes: a first input port, a first isolation port, a fourth port and a fifth port; The first port is used to input a radio frequency signal, the second port is connected to the first input port, the first isolation port is connected to the input end of the first power amplification unit, and the output end of the first power amplification unit is connected to the control end of the signal amplification unit; the fourth port is connected to one end of the first reactance unit, and the other end of the first reactance unit is grounded; the fifth port is grounded; The third port is connected to the input end of the signal amplifying unit, and the output end of the signal amplifying unit is used to output the amplified RF signal; The power divider is used to decompose the radio frequency signal into a first signal and a second signal at the first port; wherein the second port is used to output the first signal, and the third port is used to output the second signal; The first coupling unit is further used to adjust the phase of the first signal; wherein the phase shift of the first signal in the first coupling unit is related to the reactance at the fourth port; The first reactance unit is used to adjust the reactance at the fourth port; The first power amplification unit is used to amplify the first signal; The signal amplifying unit is used to amplify the second signal; wherein, under the control of the first signal input to the control end, the load impedance of the signal amplifying unit is negatively correlated with the input power of the RF signal during power backoff.

2. The power amplifier circuit according to claim 1, characterized in that: The first reactance unit includes: a first capacitor.

3. The power amplifier circuit according to claim 1, characterized in that: The power amplifier circuit further includes: a second reactance unit, the fifth port is connected to one end of the second reactance unit, and the other end of the second reactance unit is grounded; The second reactance unit is used to adjust the reactance at the fifth port to reduce the insertion loss of the first coupling unit.

4. The power amplifier circuit according to claim 3, characterized in that: A difference between a reactance value of the first reactance unit and a reactance value of the second reactance unit is smaller than a preset threshold.

5. The power amplifier circuit according to claim 4, characterized in that: The first reactance unit includes: a first capacitor, and the second reactance unit includes: a second capacitor, and a difference between a capacitance value of the first capacitor and a capacitance value of the second capacitor is smaller than the preset threshold.

6. The power amplifier circuit according to claim 1, characterized in that: The power amplifier circuit further includes: a phase compensation unit, wherein the phase compensation unit is located between the power divider and the signal amplification unit; The phase compensation unit is used to adjust the phase of the second signal so that the absolute value of the difference between the first phase difference and the second phase difference is less than or equal to a first threshold; The first phase difference is a difference between a phase of the first signal at the first isolation port and a phase of the second signal at an end of the phase compensation unit connected to the signal amplification unit when the RF signal has a first frequency; The second phase difference is a difference between a phase of the first signal at the first isolation port and a phase of the second signal at an end of the phase compensation unit connected to the signal amplification unit when the RF signal has a second frequency.

7. The power amplifier circuit according to any one of claims 1 to 6, characterized in that: The signal amplifying unit comprises: a second coupling unit, a second power amplifying unit, a third power amplifying unit and a third coupling unit; The second coupling unit includes: a second input port, a second isolation port, a sixth port and a seventh port; The third coupling unit includes: a third input port, a third isolation port, an eighth port and a ninth port; The second input port is the input end of the signal amplifying unit, the second isolation port is grounded, the sixth port is connected to the input end of the second power amplifying unit, and the output end of the second power amplifying unit is connected to the eighth port; The seventh port is connected to the input end of the third power amplification unit, the output end of the third power amplification unit is connected to the ninth port, the third isolation port is the control end of the signal amplification unit, and the third input port is used to output the amplified RF signal; The second coupling unit is used to decompose the second signal into a third signal and a fourth signal; The second power amplifying unit is used to amplify the third signal; The third power amplifying unit is used to amplify the fourth signal; The third coupling unit is used to combine the third signal and the fourth signal under the control of the first signal to obtain the amplified radio frequency signal.

8. A power amplifier circuit, characterized in that: include: A first coupling unit, a first reactance unit, a first power amplification unit and a signal amplification unit; The first coupling unit includes: a first input port, a first isolation port, a fourth port and a fifth port; The first input port is used to input a radio frequency signal, the first isolation port is connected to the input end of the first power amplification unit, and the output end of the first power amplification unit is connected to the control end of the signal amplification unit; The fourth port is connected to one end of the first reactance unit, and the other end of the first reactance unit is grounded; The fifth port is connected to the input end of the signal amplifying unit, and the output end of the signal amplifying unit is used to output the amplified radio frequency signal; The first coupling unit is used to decompose the radio frequency signal into a first signal and a second signal at the first input port; wherein the first isolation port is used to output the first signal, and the fifth port is used to output the second signal; The phase shift of the first signal at the first coupling unit is related to the reactance at the fourth port; The first reactance unit is used to adjust the reactance at the fourth port; The first power amplification unit is used to amplify the first signal; The signal amplifying unit is used to amplify the second signal; Under the control of the first signal input to the control terminal, the load impedance of the signal amplifying unit is negatively correlated with the input power of the radio frequency signal during power backoff.

9. The power amplifier circuit according to claim 8, characterized in that: The first reactance unit includes a first capacitor.

10. The power amplifier circuit according to claim 8 or 9, characterized in that: The power amplifier circuit further includes: a phase compensation unit, wherein the phase compensation unit is located between the first coupling unit and the signal amplification unit; The phase compensation unit is used to adjust the phase of the second signal so that the absolute value of the difference between the first phase difference and the second phase difference is less than or equal to a first threshold; The first phase difference is a difference between a phase of the first signal at the first isolation port and a phase of the second signal at an end of the phase compensation unit connected to the signal amplification unit when the RF signal has a first frequency; The second phase difference is a difference between a phase of the first signal at the first isolation port and a phase of the second signal at an end of the phase compensation unit connected to the signal amplification unit when the RF signal has a second frequency.

11. A communication module, characterized in that: include: A radio frequency integrated circuit and a power amplifier circuit as claimed in any one of claims 1 to 10; The radio frequency integrated circuit is used to output a radio frequency signal; The power amplifier circuit is used to amplify the radio frequency signal.

12. A communication device, characterized in that: include: An antenna and a communication module as claimed in claim 11; The communication module is used to output the amplified radio frequency signal to the antenna; The antenna is used to transmit the amplified radio frequency signal.

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