Generalized Constant Modulus Waveform Generation Method, Apparatus and Communication Device

Abstract

The present invention provides a method, apparatus and communication device for generating a generalized constant modulus waveform. The method includes: arranging single-user signal bits or multi-user signals in M rows and K columns; obtaining a real number sequence after processing K symbols in each row through a transform domain, where the real number sequence includes N real numbers; repeating the N real numbers M times, multiplying by a filter with a length of M×N points, and performing circular shift to obtain a first signal; adding up the first signals of all rows to obtain a second signal, multiplying the second signal by a phase modulation factor and performing phase modulation to obtain a generalized constant modulus waveform; or multiplying the first signal of each row by a phase modulation factor respectively and performing phase modulation to obtain the generalized constant modulus waveform of each uplink user. The proportion of the cyclic prefix in the entire symbol is small, improving the spectral efficiency; flexible range resolution and Doppler resolution can be obtained; and the out-of-band leakage can be made very low, thereby reducing the interference to out-of-band systems or adjacent channel communications.

Description

Technical Field

[0001] The present invention relates to the field of communication technologies, and in particular to a method and apparatus for generating a generalized constant modulus waveform and a communication device. Background Art

[0002] Communication perception integration is one of the key technologies for 6G. Radar waveform signals generally require constant modulus characteristics to achieve long-distance signal detection. Chirp (linear frequency modulation signal) has constant modulus characteristics and can efficiently utilize power amplifiers. By increasing the time-bandwidth product, Chirp can simultaneously improve the detection range and range resolution. Therefore, Chirp waveforms are widely used in radars. Since Chirp is a waveform designed for radars, when used for communication, it has the disadvantage of low communication data rate, and the general communication rate is several kbps. This is difficult to meet communication requirements. At the same time, the out-of-band leakage of Chirp waveforms is relatively high, causing certain interference to out-of-band systems.

[0003] Constant modulus OFDM (Orthogonal Frequency Division Multiplexing) has constant modulus characteristics and can be used for radar detection. By selecting a larger phase modulation factor h, constant modulus OFDM can generate signals with a Gaussian spectrum. The time-domain correlation peak of the radar ambiguity function graph is sharp, and it has good range resolution. However, its range resolution and Doppler resolution cannot be flexibly adjusted; the out-of-band leakage is relatively large, causing certain interference to adjacent spectrum signals. At the same time, when used for communication, a longer cyclic prefix is required for channels with a large multipath delay spread; in scenarios with a large subcarrier spacing, the symbol time-domain length is small, and at this time, the cyclic prefix accounts for a relatively large proportion of the entire symbol, which reduces the spectral efficiency. Summary of the Invention

[0004] The purpose of the embodiments of the present invention is to provide a method and apparatus for generating a generalized constant modulus waveform and a communication device, so as to solve the problem of interference to out-of-band systems and adjacent channel communications caused by the relatively high out-of-band leakage of Chirp waveforms and constant modulus OFDM waveforms in the prior art, and to solve the problems of low communication rate of Chirp waveforms, inability to flexibly adjust the range resolution and Doppler resolution of constant modulus OFDM, and low spectral efficiency of constant modulus OFDM in channels with a large multipath delay spread or a large subcarrier spacing.

[0005] To solve the above problems, the embodiments of the present invention provide a method for generating a generalized constant modulus waveform, including:

[0006] After channel encoding and modulation of single-user signal bits or multi-user signals, arrange them into M rows and K columns;

[0007] After performing transform domain processing on the K symbols in each row, obtain a real number sequence, where the real number sequence includes N real numbers;

[0008] Multiply the N real numbers by a filter of length M×N points after repeating them M times, and perform circular shift to obtain a first signal;

[0009] For a single-user signal or a downlink multi-user signal, accumulate the first signals of all rows to obtain a second signal, multiply the second signal by a phase modulation factor and then perform phase modulation to obtain a generalized constant modulus waveform; or, for an uplink multi-user signal, multiply the first signal of each row by a phase modulation factor and then perform phase modulation to obtain the generalized constant modulus waveform of each uplink user;

[0010] Wherein, the single-user signal or the multi-user signal occupies M symbols in the time domain and N subcarriers in the frequency domain; M, N, and K are all integers greater than 1.

[0011] Wherein, obtaining a real number sequence by performing transform domain processing on K symbols includes:

[0012] Perform conjugate symmetry and zero-padding operations on the K symbols to obtain N values;

[0013] Perform an orthogonal transform operation on the N values to obtain a real number sequence including N real numbers.

[0014] Wherein, obtaining a real number sequence by performing transform domain processing on K symbols includes:

[0015] Perform subcarrier mapping on the K symbols, and map the K symbols to L subcarriers;

[0016] Perform an L-point discrete Fourier transform (DFT) or other orthogonal transform operation on the L subcarriers to obtain L values;

[0017] Perform conjugate symmetry and zero-padding operations on the L values to obtain N values;

[0018] Perform an orthogonal transform operation on the N values to obtain a real number sequence including N real numbers;

[0019] Wherein, L is a positive integer not less than K.

[0020] Wherein, when the K symbols are K real number symbols, obtaining a real number sequence by performing transform domain processing on the K real number symbols includes:

[0021] Perform zero-padding operations on the K real number symbols to obtain N values;

[0022] Perform a real number orthogonal transform operation on the N values to obtain a real number sequence including N real numbers.

[0023] Among them, when the K symbols are K real number symbols, a real number sequence is obtained after processing the K real number symbols in the transform domain, including:

[0024] Perform subcarrier mapping on the K real number symbols, and map the K symbols to L subcarriers;

[0025] Perform an L-point inverse real orthogonal transform operation on the L subcarriers to obtain L values;

[0026] Perform zero-padding on the L values to obtain N values;

[0027] Perform a real orthogonal transform operation on the N values to obtain a real number sequence including N real numbers;

[0028] Among them, L is a positive integer not less than K.

[0029] Among them, the real orthogonal transform includes at least one of the following:

[0030] Hadamard transform;

[0031] Discrete cosine transform;

[0032] Discrete sine transform;

[0033] Discrete wavelet transform;

[0034] The inverse real orthogonal transform includes at least one of the following:

[0035] Inverse Hadamard transform;

[0036] Inverse discrete cosine transform;

[0037] Inverse discrete sine transform;

[0038] Inverse discrete wavelet transform.

[0039] Among them, when the K symbols are mapped to L subcarriers, the subsequent L - K subcarriers are zero elements.

[0040] Among them, the filter is a cosine filter or a raised cosine filter or other band - pass filter.

[0041] Among them, there are M larger values of the filter transformed into the frequency - domain signal.

[0042] Among them, multiplying the N real numbers repeated M times by a filter with a length of M×N points and performing circular shift to obtain the first signal includes:

[0043] Repeat the N real numbers M times to obtain M×N points;

[0044] Multiply the M×N points by a filter of length M×N;

[0045] The signal after multiplication is circularly shifted to the right to obtain a first signal; wherein, the number of shift times is (m - 1)N, m is the number of rows or the user number, m is greater than or equal to 1 and less than or equal to M.

[0046] Wherein, the phase modulation factor is 2πh; wherein, by adjusting the value of h, different spectral shapes can be obtained, and the value of h has a monotonically increasing trend with the out-of-band leakage size. That is, when h is large, the out-of-band leakage is large, and when h is small, the out-of-band leakage is small.

[0047] Wherein, the method further includes:

[0048] Adding a cyclic prefix to the generalized constant modulus waveform to obtain a single-user transmitted signal, or a downlink multi-user transmitted signal, or an uplink user transmitted signal.

[0049] Wherein, the method further includes:

[0050] Adding a zero prefix to the generalized constant modulus waveform to obtain a single-user transmitted signal, or a downlink multi-user transmitted signal, or an uplink user transmitted signal.

[0051] An embodiment of the present invention further provides a generalized constant modulus waveform generation device, including:

[0052] A first processing module, configured to perform channel coding and modulation on a single-user signal bit or a multi-user signal and then arrange it into M rows and K columns;

[0053] A second processing module, configured to obtain a real number sequence after processing the K symbols in each row in the transform domain, and the real number sequence includes N real numbers;

[0054] A third processing module, configured to repeat the N real numbers M times and then multiply them by a filter of M×N points, and perform circular shift to obtain a first signal;

[0055] A fourth processing module, configured to, for a single-user signal or a downlink multi-user signal, accumulate the first signals of all rows to obtain a second signal, multiply the second signal by a phase modulation factor and then perform phase modulation to obtain a generalized constant modulus waveform; or, for an uplink multi-user signal, multiply the first signal of each row by a phase modulation factor respectively and then perform phase modulation to obtain the generalized constant modulus waveform of each uplink user;

[0056] Wherein, the single-user signal or the multi-user signal occupies M symbols in the time domain and N subcarriers in the frequency domain; M, N, and K are all integers greater than 1.

[0057] An embodiment of the present invention further provides a communication device, including a processor and a transceiver. The transceiver receives and transmits data under the control of the processor, and the processor is used to perform the following operations:

[0058] After channel encoding and modulation of single-user signal bits or multi-user signals, arrange them into M rows and K columns;

[0059] After performing transform domain processing on the K symbols in each row, obtain a real number sequence, and the real number sequence includes N real numbers;

[0060] Repeat the N real numbers M times, then multiply them by a filter with a length of M×N points, and perform circular shift to obtain a first signal;

[0061] For single-user signals or downlink multi-user signals, accumulate the first signals of all rows to obtain a second signal, multiply the second signal by a phase modulation factor and then perform phase modulation to obtain a generalized constant modulus waveform; or, for uplink multi-user signals, multiply the first signal of each row by a phase modulation factor respectively and then perform phase modulation to obtain the generalized constant modulus waveform of each uplink user;

[0062] Wherein, the single-user signal or the multi-user signal occupies M symbols in the time domain and N subcarriers in the frequency domain; M, N, and K are all integers greater than 1.

[0063] An embodiment of the present invention further provides a communication device, including a memory, a processor, and a program stored on the memory and executable on the processor. When the processor executes the program, the above-mentioned generalized constant modulus waveform generation method is implemented.

[0064] An embodiment of the present invention further provides a computer-readable storage medium, on which a computer program is stored. When the program is executed by a processor, the steps in the above-mentioned generalized constant modulus waveform generation method are implemented.

[0065] The above technical solution of the present invention has at least the following beneficial effects:

[0066] In the generalized constant modulus waveform generation method, device and communication device of the embodiment of the present invention, waveforms are generated using two-dimensional resources in the time domain and frequency domain. By setting parameters, the frequency domain bandwidth and the number of time domain symbols can be flexibly adjusted, so that the time-bandwidth product can be adjusted. Therefore, flexible range resolution and Doppler resolution can be obtained. At the same time, a filter is added during the waveform generation process, so the out-of-band leakage can be made very low, thereby reducing the interference to out-of-band systems or adjacent channel communications. Since the time domain length of the waveform can be adjusted, in a channel with large delay spread or a scenario with large subcarrier spacing, the symbol time domain length is large. Even if a relatively long cyclic prefix is used, since the cyclic prefix accounts for a relatively small proportion of the entire symbol, the spectral efficiency of the system is improved. Description of the Drawings

[0067] Figure 1 It represents the flowchart of the steps of the generalized constant modulus waveform generation method provided by the embodiments of the present invention;

[0068] Figure 2 It represents the schematic diagram of the principle of the generalized constant modulus waveform generation method provided by the embodiments of the present invention;

[0069] Figure 3 It represents the schematic diagram of the data placement of the generalized constant modulus waveform in the generalized constant modulus waveform generation method provided by the embodiments of the present invention;

[0070] Figure 4 It represents the example diagram of the transmitted signal in the generalized constant modulus waveform generation method provided by the embodiments of the present invention;

[0071] Figure 5 It represents the example diagram of the method of transform domain processing in the generalized constant modulus waveform generation method provided by the embodiments of the present invention;

[0072] Figure 6 It represents the schematic diagram of the principle of Example 1 provided by the embodiments of the present invention;

[0073] Figure 7 It represents the schematic diagram of the principle of Example 2 provided by the embodiments of the present invention;

[0074] Figure 8 It represents the schematic diagram of the principle of Example 3 provided by the embodiments of the present invention;

[0075] Figure 9 It represents the schematic diagram of the principle of Example 4 provided by the embodiments of the present invention;

[0076] Figure 10 It represents the schematic diagram of the principle of Example 5 provided by the embodiments of the present invention;

[0077] Figure 11 It represents the schematic diagram of the principle of Example 6 provided by the embodiments of the present invention;

[0078] Figure 12 It represents the schematic diagram of the time domain signal of the filter in the generalized constant modulus waveform generation method provided by the embodiments of the present invention;

[0079] Figure 13 It represents the schematic diagram of the transformation of the time domain signal of the filter to the frequency domain signal in the generalized constant modulus waveform generation method provided by the embodiments of the present invention;

[0080] Figure 14 It represents Figure 13 The schematic diagram of the left partial enlarged signal of the frequency domain signal;

[0081] Figure 15 It represents Figure 13Schematic diagram of the right local amplified signal of the intermediate frequency domain signal;

[0082] Figure 16 One of the schematic diagrams of the out-of-band leakage of the generalized constant modulus waveform in the generalized constant modulus waveform generation method provided by the embodiment of the present invention;

[0083] Figure 17 One of the radar ambiguity function diagrams of the generalized constant modulus waveform;

[0084] Figure 18 One of the schematic diagrams of the range resolution of the generalized constant modulus waveform;

[0085] Figure 19 One of the schematic diagrams of the Doppler resolution of the generalized constant modulus waveform;

[0086] Figure 20 One of the radar ambiguity function diagrams of the generalized constant modulus waveform;

[0087] Figure 21 One of the schematic diagrams of the spectral characteristics of the generalized constant modulus waveform;

[0088] Figure 22 One of the schematic diagrams of the range resolution of the generalized constant modulus waveform;

[0089] Figure 23 One of the schematic diagrams of the Doppler resolution of the generalized constant modulus waveform;

[0090] Figure 24 Radar ambiguity function diagram of the existing constant modulus OFDM;

[0091] Figure 25 Schematic diagram of the spectral characteristics of the existing constant modulus OFDM.

[0092] Figure 26 Schematic diagram of the structure of the generalized constant modulus waveform generation device provided by the embodiment of the present invention;

[0093] Figure 27 Schematic diagram of the structure of the communication device provided by the embodiment of the present invention. Detailed implementation manners

[0094] To make the technical problems, technical solutions and advantages to be solved by the present invention clearer, the following will be described in detail with reference to the accompanying drawings and specific embodiments.

[0095] As Figure 1 and Figure 2 shown, the embodiment of the present invention provides a generalized constant modulus waveform generation method, including:

[0096] Step 101: After channel encoding and modulation of single-user signal bits or multi-user signals, they are arranged in M rows and K columns. Among them, the single-user signal or the multi-user signal occupies M symbols in the time domain and N subcarriers in the frequency domain.

[0097] Optionally, the modulation can be Pulse Amplitude Modulation (PAM) modulation, in which case the modulated signal is real; or it can be Quadrature Amplitude Modulation (QAM) modulation, in which case the modulated signal is complex. No specific limitation is made here.

[0098] Optionally, the multi-user signal includes: uplink multi-user signal, and / or downlink multi-user signal.

[0099] Step 102: After performing transform domain processing on the K symbols in each row, a real number sequence is obtained, and the real number sequence includes N real numbers.

[0100] Step 103: The N real numbers are repeated M times and then multiplied by a filter with a length of M×N points, and after cyclic shift, a first signal is obtained.

[0101] Step 104: For a single-user signal or a downlink multi-user signal, the first signals of all rows are accumulated to obtain a second signal, and the second signal is multiplied by a phase modulation factor and then phase-modulated to obtain a generalized constant modulus waveform; or, for an uplink multi-user signal, the first signal of each row is multiplied by a phase modulation factor and then phase-modulated to obtain the generalized constant modulus waveform of each uplink user.

[0102] Compared with the Chirp waveform, the generalized constant modulus waveform provided by the embodiments of the present invention has a greatly improved communication rate; the time-bandwidth product of the generalized constant modulus waveform can be flexibly adjusted, so its range resolution and Doppler resolution can be flexibly adjusted; compared with the constant modulus OFDM waveform, since the cyclic prefix accounts for a relatively small proportion of the entire symbol, the generalized constant modulus waveform has higher spectral efficiency. At the same time, due to the use of filters and some ingenious designs, the generalized constant modulus waveform has much lower out-of-band spectral leakage than the constant modulus OFDM.

[0103] As Figure 3 shown is the data placement schematic diagram of the generalized constant modulus waveform; since the signal is transmitted in the time domain and the frequency domain, a greater diversity gain can be obtained, and the performance can be better during communication; and since the time-bandwidth product N×M can be flexibly adjusted, the range resolution and Doppler resolution can be set according to needs when used for radar detection.

[0104] In other words, for single-user and downlink multi-user cases, the first signals are accumulated; for uplink multi-user cases, the first signals are not accumulated.

[0105] Among them, the phase modulation factor is 2πh; by adjusting the value of h, different spectral shapes can be obtained, and the value of h has a monotonically increasing trend with the out-of-band leakage size.

[0106] For example, the first signals of all rows are accumulated to obtain a second signal, and the second signal is multiplied by the phase modulation factor 2πh and then phase-modulated to obtain a generalized constant modulus waveform; for another example, the first signal of each row is multiplied by the phase modulation factor 2πh respectively and then phase-modulated to obtain the generalized constant modulus waveform of each uplink user.

[0107] Optionally, the fact that the value of h has a monotonically increasing trend with the out-of-band leakage size can be understood as: when h is small, the out-of-band leakage is small, and when h is large, the out-of-band leakage is large.

[0108] For example, the second signal is multiplied by 2πh, where h is the phase modulation factor, and the required generalized constant modulus waveform z is obtained by phase-modulating y according to exp(jy). Or, the first signal is multiplied by 2πh, where h is the phase modulation factor, and the required generalized constant modulus waveform z is obtained by phase-modulating y according to exp(jy).

[0109] Among them, M, N, and K are integers greater than 1 respectively.

[0110] The embodiments of the present invention generate waveforms using two-dimensional resources in the time domain and the frequency domain. By setting parameters, the frequency domain bandwidth and the number of time domain symbols can be flexibly adjusted, so that the time-bandwidth product can be adjusted. Therefore, flexible range resolution and Doppler resolution can be obtained. At the same time, a filter is added during the waveform generation process, so the out-of-band leakage can be made very low, thereby reducing the interference to out-of-band systems or adjacent channel communications. Since the time domain length of the waveform symbol is adjustable, in a channel with large delay spread or a scenario with large subcarrier spacing, the time domain length of the symbol is large, and at this time, the proportion of the cyclic prefix in the symbol length is small. Therefore, the spectral efficiency of the system can be improved.

[0111] In the embodiments of the present invention, the signal is distributed in the frequency domain and the time domain. By setting the size of the frequency domain subcarriers and the length of the time domain symbols, the time-bandwidth product of the radar waveform can be flexibly changed, and the range resolution and Doppler resolution can be flexibly changed. Further, the embodiments of the present invention use a filter, which can reduce the out-of-band leakage size; by selecting appropriate parameters, the out-of-band leakage can be 30 dB to 50 dB lower than the conventional scheme.

[0112] As an optional embodiment, the method further includes:

[0113] Such as Figure 4As shown, a cyclic prefix CP is added to the generalized constant modulus waveform to obtain a transmission signal for a single user, or a transmission signal for downlink multi-users, or a transmission signal for uplink users. Since the generalized constant modulus waveform can have a relatively large symbol length in the time domain and the cyclic prefix accounts for a relatively small proportion of the symbol length, the spectral efficiency is improved.

[0114] When the embodiment of the present invention is used for communication, since the symbol time length of the generalized constant modulus waveform is several times that of the existing method, but only one cyclic prefix is required, while multiple cyclic prefixes are required in the existing scheme, the spectral efficiency is improved. Among them, the cyclic prefix changes the cyclic convolution into a linear convolution, reducing the complexity of the receiver. At the same time, since the length of the new waveform (i.e., the generalized constant modulus waveform mentioned in this application) is M×N, compared with an OFDM symbol with a length of N points, when the subcarrier spacing of the two is the same, the time length of the generalized constant modulus waveform is M times that of OFDM. The generalized constant modulus waveform of M×N points only requires one cyclic prefix, while the M×N-point OFDM symbol requires M cyclic prefixes. Therefore, using the new waveform can improve the spectral efficiency.

[0115] As another optional embodiment, the method further includes:

[0116] A zero prefix is added to the generalized constant modulus waveform to obtain a transmission signal for a single user, or a transmission signal for downlink multi-users, or a transmission signal for uplink users.

[0117] In the embodiment of the present invention, a zero prefix is added to the generalized constant modulus waveform, that is, the prefix values of a certain length are all zeros, to obtain a transmission signal for a single user, or a transmission signal for downlink multi-users, or a transmission signal for uplink users. The advantage of using a zero prefix for the generalized constant modulus waveform is that it will not destroy the out-of-band leakage characteristic, and the out-of-band leakage is still very small.

[0118] The embodiment of the present invention uses a cyclic prefix to resist the delay spread of a multipath fading channel, but at the same time it will bring an increase in out-of-band leakage. To maintain the extremely low out-of-band leakage characteristic of the generalized constant modulus waveform, a zero cyclic prefix can be used, which will increase the complexity of the receiver to a certain extent.

[0119] In the embodiment of the present invention, there are various methods for transform domain processing. Such as Figure 5 shown:

[0120] Method 1 is to perform conjugate symmetry and zero-padding operations on K symbols to obtain N values, and perform an N-point IFFT to obtain N real values.

[0121] Method 2 is to insert zeros into K real - valued symbols (such as Pulse Amplitude Modulation), obtaining N real - valued numbers, and then performing an N - point real - valued orthogonal transform, such as Hadamard transform, Discrete Cosine Transform, Discrete Sine Transform, or Discrete Wavelet Transform, to obtain N real - valued numbers.

[0122] As an alternative embodiment, in step 102, obtaining a real - valued sequence after processing the K symbols in the transform domain includes:

[0123] Performing conjugate - symmetry and zero - insertion operations on the K symbols to obtain N values; for example, if the K symbols are [S 1 ,S 2 ,...,S K , after conjugate - symmetry and zero - insertion, we get a total of N values;

[0124] Performing an orthogonal transform operation (such as the inverse fast Fourier transform IFFT) on the N values to obtain a real - valued sequence including N real numbers.

[0125] Optionally, the filter is a cosine filter, a raised - cosine filter, or other filters.

[0126] Optionally, there are M larger values in the frequency - domain signal after the filter transformation.

[0127] As another alternative embodiment, in step 102, obtaining a real - valued sequence after processing the K symbols in the transform domain includes:

[0128] Performing sub - carrier mapping on the K symbols, mapping the K symbols to L sub - carriers;

[0129] Performing an L - point discrete Fourier transform DFT operation on the L sub - carriers to obtain L values;

[0130] Performing conjugate - symmetry and zero - insertion operations on the L values to obtain N values;

[0131] Performing an orthogonal transform operation (such as the inverse fast Fourier transform IFFT) on the N values to obtain a real - valued sequence including N real numbers;

[0132] where L is a positive integer not less than K.

[0133] As an alternative embodiment, when the K symbols in step 102 are K real - valued symbols, obtaining a real - valued sequence after processing the K real - valued symbols in the transform domain includes:

[0134] Perform zero-insertion operation on the K real number symbols to obtain N values;

[0135] Perform real orthogonal transformation operation on the N values to obtain a real number sequence including N real numbers.

[0136] As an optional embodiment, in the case where the K symbols in step 102 are K real number symbols, obtaining a real number sequence after processing the K real number symbols in the transform domain includes:

[0137] Perform subcarrier mapping on the K real number symbols, and map the K symbols to L subcarriers;

[0138] Perform L-point inverse real orthogonal transformation operation on the L subcarriers to obtain L values;

[0139] Perform zero-insertion operation on the L values to obtain N values;

[0140] Perform real orthogonal transformation operation on the N values to obtain a real number sequence including N real numbers;

[0141] Wherein, L is a positive integer not less than K.

[0142] Optionally, the real orthogonal transformation includes at least one of the following:

[0143] Hadamard transform;

[0144] Discrete cosine transform;

[0145] Discrete sine transform;

[0146] Discrete wavelet transform;

[0147] Optionally, the inverse real orthogonal transformation includes at least one of the following:

[0148] Hadamard inverse transform;

[0149] Discrete cosine inverse transform;

[0150] Discrete sine inverse transform;

[0151] Discrete wavelet inverse transform.

[0152] Wherein, in the case of mapping the K symbols to L subcarriers, the subsequent L - K subcarriers are zero elements.

[0153] Optionally, the filter is a cosine filter or a raised cosine filter or other filters.

[0154] Optionally, there are M large values in the frequency domain signal after the filter transformation.

[0155] In at least one embodiment of the present invention, step 103 includes:

[0156] Repeat the N real numbers M times to obtain M×N points;

[0157] Multiply the M×N points by a filter with a length of M×N;

[0158] Circularly shift the signal after multiplication to the right to obtain a first signal; wherein, the number of shift times is (m - 1)N, m is the number of rows or the user number, and the value of m is greater than or equal to 1 and less than or equal to M.

[0159] Optionally, the number of shift times corresponding to each row or each user is different.

[0160] To more clearly describe the generalized constant modulus waveform generation method provided by the embodiments of the present invention, the following specifically describes the method 1 of transform domain processing, and in combination with several examples, details are respectively given for single-user signals, downlink multi-user signals, and uplink multi-user signals. These examples also support the transform domain processing method 2.

[0161] Example 1, as Figure 6 shown is the first method for generating the generalized constant modulus waveform of a single user:

[0162] After the information bits of the single-user signal pass through channel coding and modulation, M×K symbols are obtained and arranged in M rows and K columns. The K symbols in each row are placed in conjugate symmetry, the first subcarrier is zero, and the middle subcarriers are filled with zeros to obtain N values. Perform an N-point IFFT operation on these N values to obtain N real numbers. Repeat the N real numbers in each row M times and multiply them by an M×N-point filter. The M×N-point filter can be a raised cosine filter or other filters. The signal in the m-th row is circularly shifted to the right by (m - 1)N points, and the signals of all rows are accumulated to obtain the final M×N-point signal x. x is a real number, multiply it by 2πh to get y, and perform phase modulation on y according to exp(jy) to obtain the required generalized constant modulus waveform z. By adjusting h, the signal bandwidth and out-of-band leakage size can be adjusted. When h is small, the out-of-band leakage is small; when h is large, the out-of-band leakage is large. When used for radar detection, the value of h needs to be greater than a certain value, and at this time, the spectrum is a Gaussian spectrum, and the signal has better time resolution.

[0163] Example 2, as Figure 7 shown is the second method for generating the generalized constant modulus waveform of a single user:

[0164] After the information bits of the single-user signal are subjected to channel coding and modulation, M×K symbols are obtained and arranged in M rows and K columns. The K symbols in each row are subjected to subcarrier mapping, mapping the K symbols to L subcarriers, and the subsequent L-K subcarriers are zero elements. Perform an L-point DFT on these L subcarriers to obtain L signals. Here, L is an integer not less than K, and L can be equal to K. After subcarrier mapping, an L-point DFT operation is performed. The result after the operation is subjected to conjugate symmetry and zero-padding operations to obtain N real numbers. Repeat the N real numbers in each row M times and multiply them point by point with an M×N-point filter. The M×N-point filter can be a raised cosine filter or other filters. The signal in the m-th row is circularly shifted to the right by (m-1)N points, and the signals of all rows are accumulated to obtain the final M×N-point signal x. x is a real number, multiply it by 2πh to get y, and perform phase modulation on y according to exp(jy) to obtain the required generalized constant modulus waveform z. By adjusting h, the signal bandwidth and out-of-band leakage size can be adjusted. When h is small, the out-of-band leakage is small; when h is large, the out-of-band leakage is large. When used for radar detection, the value of h needs to be greater than a certain value. At this time, the spectrum is a Gaussian spectrum and the signal has good time resolution.

[0165] Example 3, such as Figure 8 shown is Method 1 for generating the generalized constant modulus waveform of downlink multi-users:

[0166] Without loss of generality, assume that the user information bits are K symbols after channel coding and modulation. After conjugate symmetry and zero-padding operations, N values are obtained, and N values are obtained after performing an N-point IFFT. Repeat these N values M times to obtain M×N points, multiply them point by point with a filter of length M×N to obtain N×M values. The filter can be a raised cosine filter or other filters. Perform a circular right shift operation on this 1×MN array, and the number of shift times is (m-1)N, where m is the user number. Accumulate the values after circular shifting of all users, and multiply the accumulated result by 2πh. Multiplying by 2πh can also be done before accumulation. Finally, perform phase modulation on the result of multiplying by 2πh to obtain the required generalized constant modulus waveform z. By adjusting h, the signal bandwidth and out-of-band leakage size can be adjusted. When h is small, the out-of-band leakage is small; when h is large, the out-of-band leakage is large. When used for radar detection, the value of h needs to be greater than a certain value. At this time, the spectrum is a Gaussian spectrum and the signal has good time resolution.

[0167] Example 4, such as Figure 9 shown is Method 2 for generating the generalized constant modulus waveform of downlink multi-users:

[0168] Without loss of generality, assume that after channel coding and modulation, the user information bits are K symbols. After subcarrier mapping, the K symbols are mapped to L subcarriers, and the subsequent L - K subcarriers are zero. After L - point DFT, L values are obtained. These L values are placed in conjugate symmetry, and zeros are filled in other subcarriers to obtain N values. An N - point IFFT operation is performed on the N values. After the N - point IFFT, N real numbers are obtained, and they are repeated M times to get M×N points. These M×N points are multiplied by a filter of length M×N. The signal after multiplication is circularly shifted to the right by (m - 1)N, where m is the user number. The shifted signal is multiplied by 2πh and then accumulated. The result after accumulation is phase - modulated to obtain the desired generalized constant modulus waveform. Optionally, multiplying by 2πh can also be performed after accumulation. By adjusting h, the signal bandwidth and the out - of - band leakage size can be adjusted. When h is small, the out - of - band leakage is small; when h is large, the out - of - band leakage is large. When used for radar detection, the value of h needs to be greater than a certain value. At this time, the spectrum is a Gaussian spectrum, and the signal has good time resolution.

[0169] Example 5, as Figure 10 shown is the first method for generating the generalized constant modulus waveform of uplink multi - users:

[0170] Without loss of generality, assume that after channel coding and modulation, the user information bits are K symbols. After conjugate symmetry and zero - padding operations, N values are obtained. After performing an N - point IFFT, N real numbers are obtained. These N real numbers are repeated M times to get M×N points, which are multiplied by a filter of length M×N to obtain N×M values. The filter can be a raised - cosine filter or other filters. The array of these 1×MN numbers is circularly shifted to the right, and the number of shifts is (m - 1)N, where m is the user number. The result after shifting is multiplied by 2πh, and finally the result of multiplying by 2πh is phase - modulated to obtain the desired generalized constant modulus waveform. By adjusting h, the signal bandwidth and the out - of - band leakage size can be adjusted. When h is small, the out - of - band leakage is small; when h is large, the out - of - band leakage is large. When used for radar detection, the value of h needs to be greater than a certain value. At this time, the spectrum is a Gaussian spectrum, and the signal has good time resolution.

[0171] Example 6, as Figure 11 shown is the second method for generating the generalized constant modulus waveform of uplink multi - users:

[0172] Without loss of generality, assume that after channel coding and modulation, the user information bits are K symbols. After subcarrier mapping, the K symbols are mapped to L subcarriers, and the other L - K subcarriers are zeros. After L-point DFT, L values are obtained. These L values are placed in conjugate symmetry, and zeros are filled in other subcarriers to obtain N values. Perform an N-point IFFT operation on the N values. After the N-point IFFT, N real numbers are obtained, and they are repeated M times to get M×N points. These M×N points are multiplied by a filter of length M×N. The signal after multiplication is circularly shifted to the right by (m - 1)×N, where m is the user number. The shifted signal is multiplied by 2πh and then phase-modulated to obtain the generalized constant modulus waveform of each user. By adjusting h, the signal bandwidth and the out-of-band leakage size can be adjusted. When h is small, the out-of-band leakage is small; when h is large, the out-of-band leakage is large. When used for radar detection, the value of h needs to be greater than a certain value. At this time, the spectrum is a Gaussian spectrum, and the signal has good time resolution.

[0173] Assume that the filter of length M×N is a raised cosine filter, and its larger values in the frequency domain are M points. Figure 12 It is the time-domain signal of a filter with a length of 8192 = 256×32, that is, M = 32 and N = 256. One method for designing this filter can refer to the filter design in generalized frequency division multiplexing GFDM, such as a raised cosine filter with a roll-off factor of 0.1. Transforming it to the frequency domain gives a signal as Figure 13 shown. As Figure 14 shown, after locally magnifying the left side of the signal, there are 16 values greater than 8. As Figure 15 shown, the signal after locally magnifying the right side is as follows. The number of values greater than 8 is 16, and the total number of values greater than 8 is 32.

[0174] In an optional example, when N = 256, M = 32, h = 1.3 / (2π)≈0.2069, the filter roll-off factor is 0.3, the oversampling factor is J = 16, and K = N / J - 2 = 14, the out-of-band leakage of the obtained generalized constant modulus waveform is as Figure 16 shown. The out-of-band leakage is approximately 100 dB lower than the main lobe. N = 256 corresponds to a bandwidth of 3 MHz. When using 16QAM modulation and J = 16, considering the 1 / 2 code rate loss caused by conjugate symmetry, the communication rate when using the generalized constant modulus waveform is a data rate of 3×4 / (16×2) = 375 kbps (this data does not consider the influence of the filter and does not consider the influence of channel coding). The spectrum is a Gaussian spectrum, which indicates that it has good range resolution when used as a radar detection waveform. The radar ambiguity function diagram of the generalized constant modulus waveform is as Figure 17 shown, and its main lobe is very sharp. The range resolution is as Figure 18 shown, the main lobe is very sharp, and the side lobes are low. The Doppler resolution is as Figure 19As shown, the main lobe width is small and the frequency resolution is very high.

[0175] In another alternative example, h = 1 / (2π) ≈ 0.1592, and the ambiguity function graph of the generalized constant modulus waveform radar is as Figure 20 shown. Its main lobe is very sharp. The spectral characteristics are as Figure 21 shown. The out-of-band leakage is 70 dB smaller than the main lobe. The range resolution is as Figure 22 shown. The main lobe is very sharp and the side lobes are very low. The Doppler resolution is as Figure 23 shown. The main lobe width is small and the frequency resolution is very high.

[0176] When using the existing constant modulus OFDM as the radar waveform, its radar ambiguity function graph is as Figure 24 shown, and the spectral characteristics are as Figure 25 shown.

[0177] It can be found from the above performance comparison that the main lobe of the ambiguity function graph of the generalized constant modulus waveform radar is sharp, the out-of-band leakage of the spectrum is very low, and both the range resolution and the frequency resolution are very high. Therefore, it is a waveform with excellent performance when used for communication and sensing integration.

[0178] In summary, the embodiment of the present invention generates a waveform using two-dimensional resources in the time domain and the frequency domain. By setting parameters, the frequency domain bandwidth and the number of time domain symbols can be flexibly adjusted, so that the time-bandwidth product can be adjusted. Therefore, flexible range resolution and Doppler resolution can be obtained. At the same time, a filter is added during the waveform generation process, so the out-of-band leakage can be made very low, thereby reducing the interference to out-of-band systems or adjacent channel communications. Since the time domain length of the waveform can be adjusted, in a channel with large delay spread or a scenario with large subcarrier spacing, the time domain length of one symbol of the generalized constant modulus waveform is relatively large, and at this time, the cyclic prefix accounts for a relatively low proportion of the entire symbol. Therefore, the spectral efficiency of the system can be effectively improved.

[0179] As Figure 26 shown, the embodiment of the present invention is a generalized constant modulus waveform generation device, including:

[0180] The first processing module 2001 is configured to perform channel coding and modulation on single-user signal bits or multi-user signals and then arrange them in M rows and K columns;

[0181] The second processing module 2002 is configured to obtain a real number sequence after performing transform domain processing on K symbols in each row, and the real number sequence includes N real numbers;

[0182] The third processing module 2003 is configured to repeat the N real numbers M times, then multiply by a filter with a length of M×N points, and perform cyclic shift to obtain a first signal;

[0183] The fourth processing module 2004 is configured to, for a single-user signal or a downlink multi-user signal, accumulate the first signals of all rows to obtain a second signal, perform phase modulation on the second signal after multiplying it by a phase modulation factor to obtain a generalized constant modulus waveform; or, for an uplink multi-user signal, perform phase modulation on the first signal of each row after multiplying it by a phase modulation factor respectively to obtain the generalized constant modulus waveform of each uplink user.

[0184] Wherein, the single-user signal or the multi-user signal occupies M symbols in the time domain and N subcarriers in the frequency domain; M, N, and K are integers greater than 1 respectively.

[0185] As an optional embodiment, the second processing module is further configured to:

[0186] Perform conjugate symmetry and zero-padding operations on the K symbols to obtain N values;

[0187] Perform an orthogonal transformation operation on the N values to obtain a real number sequence including N real numbers.

[0188] As an optional embodiment, the second processing module is further configured to:

[0189] Perform subcarrier mapping on the K symbols, and map the K symbols to L subcarriers;

[0190] Perform an L-point discrete Fourier transform (DFT) or other orthogonal transformation operation on the L subcarriers to obtain L values;

[0191] Perform conjugate symmetry and zero-padding operations on the L values to obtain N values;

[0192] Perform an orthogonal transformation operation on the N values to obtain a real number sequence including N real numbers;

[0193] Wherein, L is an integer not less than K.

[0194] As an optional embodiment, when the K symbols are mapped to L subcarriers, the subsequent L - K subcarriers are zero elements.

[0195] As an optional embodiment, the filter is a cosine filter or a raised cosine filter.

[0196] As an optional embodiment, there are M large values in the frequency domain signal after the filter transformation.

[0197] As an optional embodiment, the third processing module is further configured to:

[0198] Repeat the N real numbers M times to obtain M×N points;

[0199] Multiply the M×N points by a filter of length M×N;

[0200] Circularly shift the signal after multiplication to the right to obtain a first signal; where the number of shifts is (m - 1)N, m is the number of rows or the user number, and m is greater than or equal to 1 and less than or equal to M.

[0201] As an implementable example, the phase modulation factor is 2πh; where by adjusting the value of h, different spectral shapes can be obtained, and the value of h has a monotonically increasing trend with the out-of-band leakage size.

[0202] As an alternative example, the device further includes:

[0203] A fifth processing module, configured to add a cyclic prefix to the generalized constant modulus waveform to obtain a single-user transmitted signal, or a downlink multi-user transmitted signal, or an uplink user transmitted signal.

[0204] As an alternative example, the device further includes:

[0205] A sixth processing module, configured to add a zero prefix to the generalized constant modulus waveform to obtain a single-user transmitted signal, or a downlink multi-user transmitted signal, or an uplink user transmitted signal.

[0206] In summary, the embodiments of the present invention generate waveforms using two-dimensional resources in the time domain and the frequency domain. By setting parameters, the frequency domain bandwidth and the number of time domain symbols can be flexibly adjusted, so that the time-bandwidth product is adjustable. Therefore, flexible range resolution and Doppler resolution can be obtained. At the same time, a filter is added during the waveform generation process, so the out-of-band leakage can be made very low, thereby reducing the interference to out-of-band systems or adjacent channel communications. Since the time domain length of the waveform is adjustable, in a channel with large delay spread or a scenario with large subcarrier spacing, the time domain length of the symbol is large, and at this time, the cyclic prefix accounts for a relatively low proportion of the entire symbol, improving the spectral efficiency of the system.

[0207] It should be noted that the generalized constant modulus waveform generation device provided by the embodiments of the present invention is a device capable of executing the above-mentioned generalized constant modulus waveform generation method. Then, all embodiments of the above-mentioned generalized constant modulus waveform generation method are applicable to this device, and all can achieve the same or similar beneficial effects, which will not be repeated here.

[0208] As Figure 27 shown, the embodiments of the present invention further provide a communication device, including a processor 2100 and a transceiver 2110. The transceiver 2110 receives and transmits data under the control of the processor 2100. The processor 2100 is configured to perform the following operations:

[0209] After channel encoding and modulation of single-user signal bits or multi-user signals, arrange them into M rows and K columns;

[0210] After the K symbols in each row are processed in the transform domain, a real number sequence is obtained, and the real number sequence includes N real numbers;

[0211] The N real numbers are repeated M times and then multiplied by a filter with a length of M×N points, and after circular shifting, a first signal is obtained;

[0212] For a single-user signal or a downlink multi-user signal, the first signals of all rows are accumulated to obtain a second signal, and the second signal is multiplied by a phase modulation factor and then phase-modulated to obtain a generalized constant modulus waveform; or, for an uplink multi-user signal, the first signal of each row is multiplied by a phase modulation factor and then phase-modulated to obtain the generalized constant modulus waveform of each uplink user;

[0213] Wherein, the single-user signal or the multi-user signal occupies M symbols in the time domain and N subcarriers in the frequency domain; M, N, and K are all integers greater than 1.

[0214] As an optional embodiment, the processor is further configured to perform the following operations:

[0215] Perform conjugate symmetry and zero-padding operations on the K symbols to obtain N values;

[0216] Perform an orthogonal transform operation on the N values to obtain a real number sequence including N real numbers.

[0217] As an optional embodiment, the processor is further configured to perform the following operations:

[0218] Perform subcarrier mapping on the K symbols, and map the K symbols to L subcarriers;

[0219] Perform an L-point discrete Fourier transform (DFT) operation on the L subcarriers to obtain L values;

[0220] Perform conjugate symmetry and zero-padding operations on the L values to obtain N values;

[0221] Perform an orthogonal transform operation on the N values to obtain a real number sequence including N real numbers;

[0222] Wherein, L is a positive integer not less than K.

[0223] As an optional embodiment, when the K symbols are K real number symbols, the processor is further configured to perform the following operations:

[0224] Perform zero-padding operations on the K real number symbols to obtain N values;

[0225] Perform a real number orthogonal transform operation on the N values to obtain a real number sequence including N real numbers.

[0226] As an alternative embodiment, when the K symbols are K real number symbols, the processor is further configured to perform the following operations:

[0227] Perform subcarrier mapping on the K real number symbols to map the K symbols onto L subcarriers;

[0228] Perform an L-point inverse real orthogonal transform operation on the L subcarriers to obtain L values;

[0229] Perform zero-padding on the L values to obtain N values;

[0230] Perform a real orthogonal transform operation on the N values to obtain a real number sequence including N real numbers;

[0231] Wherein, L is a positive integer not less than K.

[0232] As an alternative embodiment, the real orthogonal transform includes at least one of the following:

[0233] Hadamard transform;

[0234] Discrete cosine transform;

[0235] Discrete sine transform;

[0236] Discrete wavelet transform;

[0237] The inverse real orthogonal transform includes at least one of the following:

[0238] Hadamard inverse transform;

[0239] Discrete cosine inverse transform;

[0240] Discrete sine inverse transform;

[0241] Discrete wavelet inverse transform.

[0242] As an alternative embodiment, when mapping the K symbols onto L subcarriers, the subsequent L - K subcarriers are zero elements.

[0243] As an alternative embodiment, the filter is a cosine filter or a raised cosine filter.

[0244] As an alternative embodiment, there are M larger values of the filter-transformed frequency domain signal.

[0245] As an alternative embodiment, the processor is further configured to perform the following operations:

[0246] Repeat the N real numbers M times to obtain M × N points;

[0247] Multiply the M×N points by a filter of length M×N;

[0248] Circularly shift the signal after multiplication to the right to obtain a first signal; where the number of shifts is (m - 1)N, m is the number of rows or the user number, and m is greater than or equal to 1 and less than or equal to M.

[0249] As an optional embodiment, the phase modulation factor is 2πh; where by adjusting the value of h, different spectral shapes can be obtained, and the value of h has a monotonically increasing trend with the out-of-band leakage size.

[0250] As an optional embodiment, the processor is further configured to perform the following operations:

[0251] Add a cyclic prefix to the generalized constant modulus waveform to obtain a single-user transmitted signal, or a downlink multi-user transmitted signal, or an uplink user transmitted signal.

[0252] As an optional embodiment, the processor is further configured to perform the following operations:

[0253] Add a zero prefix to the generalized constant modulus waveform to obtain a single-user transmitted signal, or a downlink multi-user transmitted signal, or an uplink user transmitted signal.

[0254] In summary, the embodiments of the present invention generate waveforms using two-dimensional time-domain and frequency-domain resources. By setting parameters, the frequency-domain bandwidth and time-domain symbol number can be flexibly adjusted, so that the time-bandwidth product can be adjusted. Therefore, flexible range resolution and Doppler resolution can be obtained. At the same time, a filter is added during the waveform generation process, so the out-of-band leakage can be made very low, thereby reducing the interference to out-of-band systems or adjacent channel communications. Since the time-domain length of the waveform can be adjusted, in a channel with large delay spread or a scenario with large subcarrier spacing, the cyclic prefix accounts for a relatively low proportion of the entire symbol, improving the spectral efficiency of the system.

[0255] It should be noted that the communication device provided in the embodiments of the present invention is a communication device capable of executing the above-mentioned generalized constant modulus waveform generation method. Then all the embodiments of the above-mentioned generalized constant modulus waveform generation method are applicable to this communication device, and all can achieve the same or similar beneficial effects, which will not be repeated here.

[0256] The embodiments of the present invention further provide a communication device, including a memory, a processor, and a computer program stored on the memory and executable on the processor. When the processor executes the program, it implements each process in the embodiments of the above-mentioned generalized constant modulus waveform generation method, and can achieve the same technical effects. To avoid repetition, it will not be elaborated here.

[0257] An embodiment of the present invention also provides a computer-readable storage medium, on which a computer program is stored. When the program is executed by a processor, it implements each process in the embodiment of the generalized constant modulus waveform generation method described above, and can achieve the same technical effect. To avoid repetition, it will not be elaborated here. Among them, the computer-readable storage medium is, for example, a read-only memory (ROM), a random access memory (RAM), a magnetic disk, or an optical disc, etc.

[0258] Those skilled in the art should understand that the embodiments of the present application can be provided as a method, a system, or a computer program product. Therefore, the present application can take the form of a complete hardware embodiment, a complete software embodiment, or an embodiment combining software and hardware aspects. Moreover, the present application can take the form of a computer program product implemented on one or more computer-readable storage media (including but not limited to disk storage and optical storage, etc.) that contain computer-usable program code.

[0259] The present application is described with reference to the flowcharts and / or block diagrams of methods, devices (systems), and computer program products according to the embodiments of the present application. It should be understood that each process and / or block in the flowchart and / or block diagram can be implemented by computer program instructions, and the combination of the processes and / or blocks in the flowchart and / or block diagram can also be implemented by computer program instructions. These computer program instructions can be provided to the processor of a general-purpose computer, a special-purpose computer, an embedded processor, or other programmable data processing devices to generate a machine, so that the instructions executed by the processor of the computer or other programmable data processing devices generate a device for implementing the functions specified in one process Figure 1 or multiple processes and / or one block or multiple blocks.

[0260] These computer program instructions can also be stored in a computer-readable storage medium that can direct a computer or other programmable data processing device to work in a specific manner, so that the instructions stored in the computer-readable storage medium generate a paper product including an instruction device, and the instruction device implements the functions specified in one process Figure 1 or multiple processes and / or blocks Figure 1 or multiple blocks.

[0261] These computer program instructions can also be loaded onto a computer or other programmable data processing device, so that a series of operation steps are executed on the computer or other programmable device to generate a computer-implemented process. Therefore, the instructions executed on the computer or other programmable device provide steps for implementing the functions specified in one process Figure 1 or multiple processes and / or blocks Figure 1 or multiple blocks.

[0262] The above are the preferred embodiments of the present invention. It should be noted that for those of ordinary skill in the art, without departing from the principle of the present invention, several improvements and modifications can be made, and these improvements and modifications should also be regarded as the protection scope of the present invention.

Claims

1. A method for generating a generalized constant modulus waveform, characterized in that, it includes: After channel encoding and modulation of single-user signals or multi-user signals, arrange them into M rows and K columns; After performing transform domain processing on the K symbols in each row, a real number sequence is obtained, and the real number sequence includes N real numbers; Repeat the N real numbers M times, then multiply by a filter with a length of M×N points, and perform circular shift to obtain a first signal; For single-user signals or downlink multi-user signals, accumulate the first signals of all rows to obtain a second signal, multiply the second signal by a phase modulation factor and then perform phase modulation to obtain a generalized constant modulus waveform; or, for uplink multi-user signals, multiply the first signal of each row by a phase modulation factor respectively and then perform phase modulation to obtain the generalized constant modulus waveform of each uplink user; Wherein, the single-user signal or the multi-user signal occupies M symbols in the time domain and N subcarriers in the frequency domain; M, N, and K are all integers greater than 1.

2. The method according to claim 1, characterized in that, Obtaining a real number sequence after performing transform domain processing on K symbols includes: Performing conjugate symmetry and zero-padding operations on the K symbols to obtain N values; Performing an orthogonal transform operation on the N values to obtain a real number sequence including N real numbers.

3. The method according to claim 1, characterized in that, Obtaining a real number sequence after performing transform domain processing on K symbols includes: Performing subcarrier mapping on the K symbols, and mapping the K symbols to L subcarriers; Performing an L-point discrete Fourier transform (DFT) operation on the L subcarriers to obtain L values; Performing conjugate symmetry and zero-padding operations on the L values to obtain N values; Performing an orthogonal transform operation on the N values to obtain a real number sequence including N real numbers; Wherein, L is a positive integer not less than K.

4. The method according to claim 1, characterized in that, When the K symbols are K real number symbols, obtaining a real number sequence after performing transform domain processing on the K real number symbols includes: Performing zero-padding operations on the K real number symbols to obtain N values; Performing a real number orthogonal transform operation on the N values to obtain a real number sequence including N real numbers.

5. The method according to claim 1, characterized in that, When the K symbols are K real number symbols, obtaining a real number sequence after performing transform domain processing on the K real number symbols includes: Performing subcarrier mapping on the K real number symbols, and mapping the K symbols to L subcarriers; Performing an L-point inverse real number orthogonal transform operation on the L subcarriers to obtain L values; Performing zero-padding operations on the L values to obtain N values; Performing a real number orthogonal transform operation on the N values to obtain a real number sequence including N real numbers; Wherein, L is a positive integer not less than K.

6. The method according to claim 4 or 5, characterized in that, The real number orthogonal transform includes at least one of the following: Hadamard transform; Discrete cosine transform; Discrete sine transform; Discrete wavelet transform; The inverse real number orthogonal transform includes at least one of the following: Hadamard inverse transform; Discrete cosine inverse transform; Inverse discrete sine transform; Inverse discrete wavelet transform.

7. The method according to claim 3 or 5, characterized in that when mapping the K symbols to L subcarriers, the subsequent L - K subcarriers are zero elements.

8. The method according to claim 1, characterized in that the filter is a cosine filter or a raised - cosine filter.

9. The method according to claim 1 or 8, characterized in that there are M large values in the frequency - domain signal after the filter transformation.

10. The method according to claim 1, characterized in that the step of multiplying the N real numbers repeated M times by a filter of length M×N points and performing a cyclic shift to obtain a first signal includes: repeating the N real numbers M times to obtain M×N points; multiplying the M×N points by a filter of length M×N; cyclically shifting the multiplied signal to the right to obtain a first signal; where the number of shift times is (m - 1)N, m is the number of rows or the user number, and m is greater than or equal to 1 and less than or equal to M.

11. The method according to claim 1, characterized in that the phase - modulation factor is 2πh; where by adjusting the value of h, different spectral shapes can be obtained, and the value of h has a monotonically increasing trend with the out - of - band leakage size.

12. The method according to claim 1, characterized in that the method further includes: adding a cyclic prefix to the generalized constant - modulus waveform to obtain a single - user transmitted signal, or a downlink multi - user transmitted signal, or an uplink user transmitted signal.

13. The method according to claim 1, characterized in that the method further includes: adding a zero prefix to the generalized constant - modulus waveform to obtain a single - user transmitted signal, or a downlink multi - user transmitted signal, or an uplink user transmitted signal.

14. A generalized constant - modulus waveform generating device, characterized in that comprising: a first processing module for channel - encoding and modulating a single - user signal bit or a multi - user signal and then arranging it into M rows and K columns; a second processing module for obtaining a real - number sequence after transform - domain processing of the K symbols in each row, the real - number sequence including N real numbers; a third processing module for multiplying the N real numbers repeated M times by a filter of length M×N points and performing a cyclic shift to obtain a first signal; a fourth processing module for, for a single - user signal or a downlink multi - user signal, adding all rows of the first signals to obtain a second signal, multiplying the second signal by a phase - modulation factor and then performing phase modulation to obtain a generalized constant - modulus waveform; or, for an uplink multi - user signal, multiplying each row of the first signals by a phase - modulation factor and then performing phase modulation to obtain the generalized constant - modulus waveform of each uplink user; wherein the single - user signal or the multi - user signal occupies M symbols in the time domain and N subcarriers in the frequency domain; M, N, and K are all integers greater than 1.

15. A communication device, comprising a processor and a transceiver, the transceiver receiving and sending data under the control of the processor, characterized in that the processor is used to perform the following operations: After channel encoding and modulation of single-user signal bits or multi-user signals, they are arranged in M rows and K columns; After subjecting the K symbols in each row to transform domain processing, a real number sequence is obtained, and the real number sequence includes N real numbers; The N real numbers are repeated M times and then multiplied by a filter with a length of M×N points, and after circular shift, a first signal is obtained; For a single-user signal or a downlink multi-user signal, the first signals of all rows are accumulated to obtain a second signal, and the second signal is multiplied by a phase modulation factor and then subjected to phase modulation to obtain a generalized constant modulus waveform; or, for an uplink multi-user signal, the first signal of each row is multiplied by a phase modulation factor and then subjected to phase modulation to obtain the generalized constant modulus waveform of each uplink user; Wherein, the single-user signal or the multi-user signal occupies M symbols in the time domain and N subcarriers in the frequency domain; M, N, and K are all integers greater than 1.

16. A communication device, comprising a memory, a processor, and a program stored on the memory and executable on the processor; Characterized in that, When the processor executes the program, it implements the generalized constant modulus waveform generation method according to any one of claims 1-13.

17. A computer-readable storage medium, on which a computer program is stored, Characterized in that, When the program is executed by a processor, it implements the steps in the generalized constant modulus waveform generation method according to any one of claims 1-13.

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