Complex vector current control method of duplex winding induction AC / DC generator system

Abstract

The invention discloses a complex vector current control method for a duplex-winding induction AC / DC generator system, and relates to the field of duplex-winding induction motors, and the method introduces a complex vector current controller in the current control of a duplex-winding induction generator, and achieves the precise tracking of a phase current through the control of the phase voltage of a winding. Meanwhile, a cross coupling term in a countermeasure power winding is also considered, and decoupling control is performed by designing complex vector current and utilizing a decoupling term, so that interference between the power winding and a control winding is reduced, and a double-winding motor system can be ensured to stably perform current control at a high rotating speed; therefore, better decoupling control can be realized under the condition of high-rotating-speed alternating-current and direct-current power generation of the duplex-winding induction generator, the current decoupling effect under the high rotating speed is improved, the system performance is improved, and the system performance and parameter robustness during high-rotating-speed alternating-current and direct-current power generation control of the duplex-winding induction generator are effectively improved.

Description

Technical Field

[0001] The present application relates to the field of dual-winding induction motors, and in particular to a complex vector current control method for a dual-winding induction AC / DC generator system. Background Art

[0002] More-electric engine technology uses a new electromechanical structure to optimize the conversion performance of secondary energy in the secondary energy generation system. One of the main key technologies is to embed the generator and starter / generator into the engine to form a mechatronic structure. Therefore, in the context of more-electric engines, the design and optimization of aircraft generators have an important research position. With the development of electric propulsion systems in aerospace, aircraft have an increasing demand for high-performance motors. The propulsion systems of electric aircraft, drones, and other space equipment are increasingly dependent on electric drives, and the control flexibility and fault redundancy of traditional single-winding motors cannot meet the requirements of these high-end applications. Therefore, the development of dual-winding motors has become a natural choice to meet these high power density, high reliability, and high fault tolerance requirements.

[0003] Compared with other motors, the development of dual-winding induction motors in the aerospace field has a unique technical background and requirements. Its development is mainly to meet the aircraft system's requirements for high-efficiency, multi-functional, high-reliability and fault-tolerant motor drives. However, the magnetic fields generated by the two stator winding currents of the dual-winding induction motor interact with each other, and the current of the control-side winding and the current of the power-side winding will affect each other, resulting in the risk of instability of the traditional PI current control under high-speed conditions of the dual-winding induction motor power generation system, and the system control stability is low. Summary of the invention

[0004] In view of the above problems and technical requirements, this application proposes a complex vector current control method for a dual-winding induction AC / DC generator system. The technical solution of this application is as follows:

[0005] A complex vector current control method for a dual-winding induction AC / DC generator system, the complex vector current control method comprising:

[0006] The expected DC voltage value U dcref The DC voltage amplitude U across the DC load connected to the control winding of the double-winding induction motor dc The error is input into the PI controller to obtain the q-axis reference current i of the control winding cqref ; Set the AC voltage expected value U pacref The effective value of the AC voltage U across the AC load connected to the power winding of a double-winding induction motor pac After making the difference, input it into the PI controller to get the d-axis reference current i of the control winding cdref ;

[0007] according to Design the d-axis current loop to obtain the d-axis given voltage of the control winding, according to Design the q-axis current loop to obtain the q-axis given voltage of the control winding; where i cd is the d-axis current of the control winding, i cq is the q-axis current of the control winding, K p is the proportional term coefficient, K i is the integral term coefficient, K c is the decoupling term coefficient and is related to the real-time electrical angular velocity ω of the dual-winding induction motor e Related, s is the Laplace transform variable in the complex frequency domain;

[0008] A power converter connected to a control winding of a dual-winding induction motor is controlled using vector modulation based on a d-axis given voltage and a q-axis given voltage of the control winding.

[0009] Its further technical solution is that the proportional term coefficient K p , integral term coefficient K i , decoupling coefficient K c The calculation formula is:

[0010]

[0011] Where ω is the system design bandwidth, R c ′ is the equivalent resistance of the control winding and R c is the resistance of the control winding, R r is the equivalent rotor resistance, ω e is the real-time electrical angular velocity of the dual-winding induction motor, L c is the inductance of the control winding, L r is the rotor equivalent inductance, L m It is the main inductance of the double-winding induction motor.

[0012] A further technical solution is that the complex vector current control method further includes:

[0013] The flux amplitude ψ is obtained based on the phase current of the control winding and the phase current of the power winding of the dual-winding induction motor. r ;

[0014] According to the magnetic flux amplitude ψ r Disturbance compensation items are added to the d-axis current loop and the q-axis current loop respectively to perform disturbance compensation.

[0015] A further technical solution is to use the magnetic flux amplitude ψ r The disturbance compensation for the d-axis current loop includes:

[0016] For the d-axis current loop Add the d-axis disturbance compensation term to the output of

[0017] Among them, L r is the rotor equivalent inductance, T r is the time constant of the two-winding induction motor and T r =L r / R r ′, R r is the equivalent rotor resistance, L m It is the main inductance of the double-winding induction motor.

[0018] A further technical solution is to use the magnetic flux amplitude ψ r The disturbance compensation for the q-axis current loop includes:

[0019] For the q-axis current loop Add the q-axis disturbance compensation term to the output Among them, ω r is the rotor flux angular velocity and ω r =(1-ζ)·ω e , ζ is the slip rate.

[0020] A further technical solution is that the observed magnetic flux amplitude in:

[0021]

[0022] Among them, T r is the time constant of the two-winding induction motor and T r =L r / R r ′, R r is the equivalent rotor resistance, L r is the rotor equivalent inductance, L m is the main inductance of the double-winding induction motor; p is the differential operator; ω r is the rotor flux angular velocity and ω r =(1-ζ)·ω e ,ζ is the slip rate;i cα and i cβ are the α-axis current and β-axis current converted from the phase current of the control winding, i pα and i pβ They are the α-axis current and β-axis current obtained by converting the phase current of the power winding.

[0023] A further technical solution is that the complex vector current control method further includes:

[0024] In the d-axis current loop, The output of is passed through the delay compensator and then the d-axis disturbance compensation term is added to obtain the d-axis given voltage;

[0025] In the q-axis current loop, The output of is passed through the delay compensator and then the q-axis disturbance compensation term is added to obtain the q-axis given voltage;

[0026] Among them, the transfer functions of the delay compensators in the d-axis current loop and the q-axis current loop are And phase lead compensation is performed, K is the gain of the delay compensator, T1 and T2 are the zero and pole time constants of the phase lead compensation respectively, and T1>T2.

[0027] Its further technical solution is:

[0028] Where ω is the system design bandwidth, φ m is the desired phase boost angle.

[0029] A further technical solution is that the complex vector current control method further includes:

[0030] In the d-axis current loop, A low-pass filter is also provided between the output and the delay compensator;

[0031] In the q-axis current loop, A low-pass filter is also provided between the output and the delay compensator;

[0032] Among them, the transfer functions of the low-pass filters in the d-axis current loop and the q-axis current loop are T is the cutoff frequency of the low pass filter.

[0033] A further technical solution is that the cut-off frequency T of the low-pass filter is set to the switching frequency of the switch tube.

[0034] The beneficial technical effects of this application are:

[0035] The present application discloses a complex vector current control method for a dual-winding induction AC / DC generator system. The method introduces a complex vector current controller into the current control of the dual-winding induction generator, realizes accurate tracking of the phase current of the control winding by controlling the phase voltage of the winding, and also considers the cross-coupling term in the counteracting power winding. The interference between the power winding and the control winding is reduced by designing a complex vector current decoupling control, ensuring that the dual-winding motor system can stably control the current at high speed, thereby achieving better decoupling control in the high-speed AC / DC power generation of the dual-winding induction generator, and obtaining higher control accuracy in the dynamic performance of the motor. The scheme improves the current decoupling effect at high speed and improves the system performance. When the parameters of the dual-winding induction generator change, it still guarantees a good control effect, effectively improving the system performance and parameter robustness of the dual-winding induction motor during high-speed AC / DC power generation control.

[0036] This method further compensates the current loop by designing a flux observer, further improving the current loop control accuracy reduction and system oscillation problems of the dual-winding induction motor at high speeds. Secondly, the phase lag and delay problems in the system are compensated by phase compensation, the oscillation caused by high-frequency noise is weakened by designing a filtering link, and the gain of the control system in the high-frequency band is reduced to improve the frequency response characteristics of the system. BRIEF DESCRIPTION OF THE DRAWINGS

[0037] Figure 1 It is a system control block diagram of a complex vector current control method of a dual-winding induction AC / DC generator system according to an embodiment of the present application.

[0038] Figure 2 It is the traditional PI current control block diagram.

[0039] Figure 3 It is a scalar structure diagram of a dual-winding induction motor in the present application taking into account the delay.

[0040] Figure 4 It is a control block diagram of a complex vector current controller in one embodiment of the present application. DETAILED DESCRIPTION

[0041] The specific implementation of the present application is further described below in conjunction with the accompanying drawings.

[0042] This application discloses a complex vector current control method for a dual-winding induction AC / DC generator system. Please refer to Figure 1As shown in the system control block diagram, in the dual-winding induction AC / DC generator system, the dual-winding induction motor includes a control winding and a power winding. The control winding of the dual-winding induction motor is connected to the power converter, and the starting power supply is connected to the DC bus of the power converter. In addition, the control winding is also connected to the DC load for DC power supply. The power winding of the dual-winding induction motor is connected to the AC load for AC power supply. Figure 1 Taking a five-phase-three-phase double-winding induction motor as an example, the control winding includes five-phase windings A, B, C, D, and E, and the power winding includes three-phase windings F, G, and H.

[0043] During the operation of the dual-winding induction AC / DC generator, the phase currents of each phase of the control winding are collected, such as Figure 1 in,i a 、i b 、i c 、i d 、i e The phase currents of the five-phase control windings A, B, C, D, and E are respectively. Then, the α-axis current i of the control winding in the αβ coordinate system can be obtained by performing Clarke transformation on the phase current of each phase control winding. cα and the β-axis current i cβ Further park transformation can be performed to obtain the d-axis current i of the control winding in the dq coordinate system cd and q-axis current i cq The traditional PI current control method is to obtain and convert the d-axis current i cd and q-axis current i cq Afterwards, Figure 2 As shown, the expected value of the d-axis current i cdcmd and d-axis current i cd After the difference is made, it passes through the PI controller to output the d-axis given voltage u cd1 and u cd3 , where u cd1 is the given standard voltage component in the d-axis direction, u cd3 is the third harmonic given voltage component in the d-axis direction. Similarly, the q-axis current expected value i cqcmd and q-axis current i cq After the difference is made, it passes through the PI controller to output the q-axis given voltage u cq1 and u cq3 , where u cq1 is the given standard voltage component in the q-axis direction, u cq3 It is the third harmonic given voltage component in the q-axis direction. Then, based on the d-axis given voltage and the q-axis given voltage, the power converter connected to the control winding of the double-winding induction AC / DC generator is controlled by vector modulation.

[0044] For a dual-winding induction motor, the voltage equation in the dq coordinate system is:

[0045]

[0046] Among them, R c is the control winding resistance, R p is the power winding resistance, R r is the equivalent rotor resistance. Where, ψ cd , cq , pd , pq , rd , rq are all current flux components and:

[0047]

[0048] Among them, u cd and u cq is the phase voltage of the control winding in the dq coordinate system, i cd and i cq is the phase current of the control winding in the dq coordinate system. pd and u pq is the phase voltage of the power winding in the dq coordinate system, i pd and i pq is the phase current of the power winding in the dq coordinate system, i rd and i rq is the current of the rotor equivalent circuit in the dq coordinate system. e is the real-time electrical angular velocity, ω s is the slip frequency. c is the inductance of the control winding, L p is the inductance of the power winding, L r is the rotor equivalent inductance, L m is the main inductance of the double-winding induction motor. t represents time.

[0049] It can be seen from the above equations (1) and (2) that there is a magnetic field coupling effect between the control winding and the power winding of the dual-winding induction motor. This magnetic field coupling effect gradually intensifies with the increase of the speed, causing the phase current of the control winding and the phase current of the power winding to affect each other and introduce additional cross-coupling terms. It is precisely because of these cross-coupling terms that the use of Figure 2 The traditional PI current control shown is prone to instability under high speed conditions.

[0050] For this purpose, this application introduces a complex vector current control method. In the dual-winding induction motor power generation vector control, the rotor flux orientation can realize the decoupling control of the current flux component and the torque component. The d-axis of the two-phase rotating coordinate system is fixed on the rotor flux vector. At this time, there is a flux amplitude ψ r =ψrd And rq =0, from this we can know:

[0051]

[0052] Substituting equation (3) into equations (1) and (2) for calculation, we can obtain the dq axis phase voltage u of the control winding: cd and u cq The voltage amplitude calculation formula between:

[0053]

[0054] in, Equivalent resistance of control winding T r is the time constant of the two-winding induction motor and T r =L r / R r ′, p is the differential operator. Based on formula (4), the scalar structure diagram of the double-winding induction motor can be obtained as follows: Figure 3 As shown, It represents the relationship between the given voltage of the control winding and the given current of the power winding. Specifically, Z load represents the power winding load impedance of the double-winding induction motor, S(Φ) represents the magnetic saturation factor of the double-winding induction motor, k w represents the pole arc coefficient, and N2 / N1 is the turns ratio of the stator power winding to the control winding. In the above process, there is actually a calculation delay τ d , so the final output takes into account the calculation delay τ d The phase current of the control winding in the dq coordinate system after and And the phase current of the power winding in the dq coordinate system and

[0055] Based on formula (4), the voltage calculation function of the complex vector current controller suitable for the dual-winding induction AC / DC generator system can be established as:

[0056]

[0057] The first part of formula (5) represents the resistance and inductance coupling terms between the phase voltage and phase current of the control winding, and the third part represents the disturbance term of the power winding current. These two parts are the most important considerations when designing a complex vector current controller. The main design goal of the first part of formula (5) in the complex vector current controller is to accurately track the phase current of the control winding by controlling the phase voltage of the control winding, and the main design goal of the third part of formula (5) in the complex vector current controller is to counteract the cross-coupling term in the power winding. Based on this consideration, the control block diagram of the complex vector current controller of the present application is as follows: Figure 4 Using the complex vector current controller of the present application, during the operation of the dual-winding induction AC / DC generator system, in addition to collecting the phase current of the control winding, the DC voltage amplitude U at both ends of the DC load connected to the control winding of the dual-winding induction AC / DC generator is also obtained. dc And the AC voltage RMS value U across the AC load connected to the power winding pac .

[0058] The expected DC voltage value U dcref The DC voltage amplitude U across the DC load dc The error is input into the PI controller to obtain the q-axis reference current i of the control winding cqref . And the AC voltage expected value U pacref The AC voltage RMS value U across the AC load pac After making the difference, input it into the PI controller to get the d-axis reference current i of the control winding cdref .

[0059] Then the d-axis reference current i cdref , q-axis reference current i cqref , d-axis current i cd and q-axis current i cq Input the complex vector current controller designed in this application to obtain the d-axis given voltage u cdref and q-axis given voltage u cqref In the designed complex vector current controller:

[0060] according to Design the d-axis current loop to obtain the d-axis given voltage of the control winding. Design the q-axis current loop to obtain the q-axis given voltage of the control winding. p is the proportional term coefficient, K i is the integral term coefficient, K c is the decoupling term coefficient and is related to the real-time electrical angular velocity ω of the dual-winding induction motor e Related, s is the Laplace transform variable in the complex frequency domain.

[0061] Proportional term coefficient K p, integral term coefficient K i , decoupling coefficient K c The motor parameters of the dual-winding induction motor are used for tuning, and:

[0062]

[0063] Where ω is the system design bandwidth, R c ' is the equivalent resistance of the control winding and the calculation formula is as recorded above, L c is the inductance of the control winding, L r is the rotor equivalent inductance, L m is the main inductance of the double-winding induction motor. e It is the real-time electrical angular velocity of the dual-winding induction motor, which can be obtained by collecting the speed n of the dual-winding induction motor and using Calculated, where p0 is the number of generator pole pairs.

[0064] The above method can be used to design complex vector current decoupling to reduce interference between the power winding and the control winding, thereby ensuring that the dual-winding induction AC / DC generator system can stably control current at high speeds and increase the robustness of the system.

[0065] On this basis, it can be seen from formula (5) that the calculation formula of the phase voltage of the control winding also includes the second part, which is the flux cross-coupling term. In one embodiment, in order to further improve the current loop control accuracy reduction and system oscillation problems of the dual-winding induction motor in high-speed situations, the constant rotor flux disturbance term of the dual-winding induction motor is also considered in the design of the complex vector current controller for feedforward compensation. Therefore, in another embodiment, Figure 1 As shown, during the operation of the dual-winding induction motor, the phase current of the power winding is also collected, such as Figure 1 i f 、i g 、i h They are the phase currents of the three-phase power windings F, G, and H respectively. Similarly, by performing Clarke transformation on the phase currents of each phase power winding, we can obtain the α-axis current i of the power winding in the αβ coordinate system pα and the β-axis current i pβ .

[0066] Control winding α-axis current i cα and the β-axis current i cβ And the α-axis current i of the power winding pα and the β-axis current i pβ The flux observer is then used to obtain the flux amplitude ψ according to the phase current of the control winding and the phase current of the power winding of the dual-winding induction motor. r. Magnetic flux amplitude ψ r The observed value of is obtained by taking the root mean square of the magnetic flux on the α-axis and the β-axis:

[0067]

[0068] Among them, the magnetic flux on the α-axis and β-axis is obtained by the following formula:

[0069]

[0070] In the above formula, ω r is the rotor flux angular velocity and ω r =(1-ζ)·ω e , ζ is the slip rate.

[0071] The observed magnetic flux amplitude ψ r Then, according to the magnetic flux amplitude ψ r Disturbance compensation items are added to the d-axis current loop and the q-axis current loop respectively to perform disturbance compensation.

[0072] For the d-axis current loop, the d-axis disturbance compensation term is added to After the output of , the added d-axis disturbance compensation term is

[0073] For the q-axis current loop, the q-axis disturbance compensation term is added to After the output of , the added q-axis disturbance compensation term is

[0074] Furthermore, considering that the calculation delay of the dual-winding induction motor is more significant than that of the ordinary asynchronous motor, in another embodiment, a delay compensator is also provided in the d-axis current loop and the q-axis current loop, respectively. Figure 4 :

[0075] In the d-axis current loop, The output of is passed through the delay compensator and then the d-axis disturbance compensation term is added to obtain the d-axis given voltage.

[0076] In the q-axis current loop, The output of is passed through the delay compensator and then the q-axis disturbance compensation term is added to obtain the q-axis given voltage.

[0077] The delay compensator is used to compensate for the system phase lag caused by processor calculation, sampling processing, and PWM modulation. Phase advance compensation is adopted. The transfer functions of the delay compensators in the d-axis current loop and the q-axis current loop are:

[0078]

[0079] Where K is the gain of the delay compensator, which is freely selected according to the system default gain. T1 and T2 are the zero and pole time constants of the phase lead compensation, respectively, and T1>T2. In one embodiment, the selection configuration of T1 and T2 is adjusted by the following formula:

[0080]

[0081] Where ω is the system design bandwidth, φ m is the required phase boost angle, which can be set according to the actual system conditions. m Compensate for 10 to 30 degrees.

[0082] Furthermore, considering that the system interference noise of the dual-winding induction motor is more significant than that of the ordinary asynchronous motor, in another embodiment, low-pass filters are also set in the d-axis current loop and the q-axis current loop, respectively. Figure 4 :

[0083] In the d-axis current loop, A low-pass filter is also provided between the output and the delay compensator.

[0084] In the q-axis current loop, A low-pass filter is also provided between the output and the delay compensator.

[0085] The low-pass filter is used to filter the system interference noise. The transfer functions of the low-pass filters in the d-axis current loop and the q-axis current loop are:

[0086]

[0087] Wherein, T is the cut-off frequency of the low-pass filter. In one embodiment, the cut-off frequency T of the low-pass filter is set to the switching frequency of the switch tube, so as to filter out the high-frequency noise of the current loop in the dual-winding induction motor.

[0088] In summary, in the d-axis current loop, The output of is first filtered by a low-pass filter to remove noise, then passed through a delay compensator for phase advance compensation, and finally the d-axis disturbance compensation term is superimposed. The final output d-axis given voltage includes u cd1 and u cd3 . In the q-axis current loop, The output of is first filtered by a low-pass filter to remove noise, then passed through a delay compensator for phase advance compensation, and finally the q-axis disturbance compensation term is superimposed. The final output q-axis given voltage includes u cq1 and u cq3 .

Claims

1. A complex vector current control method for a dual-winding induction AC / DC generator system, characterized in that: The complex vector current control method comprises: The expected DC voltage value U dcref The DC voltage amplitude U across the DC load connected to the control winding of the double-winding induction motor dc The error is input into the PI controller to obtain the q-axis reference current i of the control winding cqref ; Set the AC voltage expected value U pacref The effective value of the AC voltage U across the AC load connected to the power winding of a double-winding induction motor pac After making the difference, input it into the PI controller to get the d-axis reference current i of the control winding cdref ; according to Design the d-axis current loop to obtain the d-axis given voltage of the control winding, according to Design the q-axis current loop to obtain the q-axis given voltage of the control winding; where i cd is the d-axis current of the control winding, i cq is the q-axis current of the control winding, K p is the proportional term coefficient, K i is the integral term coefficient, K c is the decoupling term coefficient and is related to the real-time electrical angular velocity ω of the dual-winding induction motor e Related, s is the Laplace transform variable in the complex frequency domain; A power converter connected to a control winding of a dual-winding induction motor is controlled using vector modulation based on a d-axis given voltage and a q-axis given voltage of the control winding.

2. The complex vector current control method according to claim 1, characterized in that: Proportional term coefficient K p , integral term coefficient K i , decoupling coefficient K c The calculation formula is: Where ω is the system design bandwidth, R c ′ is the equivalent resistance of the control winding and R c is the resistance of the control winding, R r is the equivalent rotor resistance, ω e is the real-time electrical angular velocity of the dual-winding induction motor, L c is the inductance of the control winding, L r is the rotor equivalent inductance, L m It is the main inductance of the double-winding induction motor.

3. The complex vector current control method according to claim 1, characterized in that: The complex vector current control method further includes: The flux amplitude ψ is obtained based on the phase current of the control winding and the phase current of the power winding of the dual-winding induction motor. r ; According to the magnetic flux amplitude ψ r Disturbance compensation items are added to the d-axis current loop and the q-axis current loop respectively to perform disturbance compensation.

4. The complex vector current control method according to claim 3, characterized in that: According to the magnetic flux amplitude ψ r The disturbance compensation for the d-axis current loop includes: For the d-axis current loop Add the d-axis disturbance compensation term to the output of Among them, L r is the rotor equivalent inductance, T r is the time constant of the two-winding induction motor and T r =L r / R r ′, R r is the equivalent rotor resistance, L m It is the main inductance of the double-winding induction motor.

5. The complex vector current control method according to claim 3, characterized in that: According to the magnetic flux amplitude ψ r The disturbance compensation for the q-axis current loop includes: For the q-axis current loop Add the q-axis disturbance compensation term to the output Among them, ω r is the rotor flux angular velocity and ω r =(1-ζ)·ω e , ζ is the slip rate.

6. The complex vector current control method according to claim 3, characterized in that: Observed flux amplitude in: Among them, T r is the time constant of the two-winding induction motor and T r =L r / R′ r , R r is the equivalent rotor resistance, L r is the rotor equivalent inductance, L m is the main inductance of the double-winding induction motor; p is the differential operator; ω r is the rotor flux angular velocity and ω r =(1-ζ)·ω e ,ζ is the slip rate;i cα and i cβ are the α-axis current and β-axis current converted from the phase current of the control winding, i pα and i pβ They are the α-axis current and β-axis current obtained by converting the phase current of the power winding.

7. The complex vector current control method according to claim 3, characterized in that: The complex vector current control method further includes: In the d-axis current loop, The output of is passed through the delay compensator and then the d-axis disturbance compensation term is added to obtain the d-axis given voltage; In the q-axis current loop, The output of is passed through the delay compensator and then the q-axis disturbance compensation term is added to obtain the q-axis given voltage; Among them, the transfer functions of the delay compensators in the d-axis current loop and the q-axis current loop are And phase lead compensation is performed, K is the gain of the delay compensator, T1 and T2 are the zero and pole time constants of the phase lead compensation respectively, and T1>T2.

8. The complex vector current control method according to claim 7, characterized in that: Where ω is the system design bandwidth, φ m is the desired phase boost angle.

9. The complex vector current control method according to claim 7, characterized in that: The complex vector current control method further includes: In the d-axis current loop, A low-pass filter is also provided between the output and the delay compensator; In the q-axis current loop, A low-pass filter is also provided between the output and the delay compensator; Among them, the transfer functions of the low-pass filters in the d-axis current loop and the q-axis current loop are T is the cutoff frequency of the low pass filter.

10. The complex vector current control method according to claim 9, characterized in that: The cut-off frequency T of the low-pass filter is set to the switching frequency of the switch tube.

Images