Trans-impedance type flip voltage following driving linear voltage regulator

Abstract

The invention provides a transimpedance type flip voltage following driving linear voltage regulator, which comprises a control module and a transimpedance type flip voltage follower, namely a TIFVF module, and is characterized in that the control module comprises an error amplifier and a voltage-current converter which are connected in series; the output voltage Vout passes through a selectable divider resistor and then is fed back to an error amplifier to be compared with the reference voltage Vref to obtain an error signal, the error signal is amplified and conditioned by a compensation network to obtain a control voltage signal Vctrl, and the control voltage signal Vctrl passes through a voltage-current conversion circuit to obtain a current control signal Ictrl required by the TIFVF; the whole forms a negative feedback loop, and two links of error amplifier-voltage and current conversion provide enough loop gain.

Description

Technical Field

[0001] The present invention relates to the field of linear voltage regulators, and more particularly to a transimpedance flip voltage follower driven linear voltage regulator. Background Art

[0002] As the key interface between signal processing units and power devices, the performance of the driver circuit directly affects the efficiency and stability of the entire electronic system. Looking back at the development of driver circuits, we can clearly see the technological evolution path from traditional source followers to flip-type voltage follower (FVF) circuits. Early driver circuits mainly used a simple source follower structure, which had a high output impedance and could not meet the driving capability requirements of modern electronic devices. With the advancement of technology, researchers proposed FVF circuits based on the principle of negative feedback. Through the local negative feedback structure, the output resistance is reduced by several to dozens of times, significantly improving the driving performance of the circuit.

[0003] The development of low-dropout linear regulator (LDO) technology has paved the way for the application of FVF circuits. Traditional LDO circuits employ a voltage divider consisting of upper and lower resistors in parallel with a compensation capacitor. While this provides a leading zero, when the resistor ratio is small, the zero and pole are very close, significantly reducing the phase compensation effect. To address this issue, academics have proposed various improvements, including transconductance gain enhancement architectures and the use of voltage-controlled current sources for compensation. These advances have laid the theoretical foundation for the emergence of FVF voltage-flipping driver circuits.

[0004] In recent years, with the widespread adoption of SoC chips, the demand for high-performance LDO circuits has increased dramatically. FVF LDOs, with FVF control modules at their core, have attracted significant attention due to their exceptional performance in low power consumption, high load current, high power supply rejection ratio, and transient response.

[0005] FVF type LDO has become popular in recent years. The core of FVF is as follows: Figure 1 As shown, the external control module adjusts V CTRL The FVF structure achieves a fast response to load current changes through the local feedback loop Mp1-Mn1-Mpower.

[0006] However, compared to traditional LDO structures, the DC error is large and the load regulation is poor, requiring additional compensation for high loop gain to suppress it. In addition, the power supply rejection ratio is also worse than that of traditional LDOs, and its output voltage swing is limited by the Vgs of the MP1 tube. On the other hand, the main function of FVF and traditional LDOs is to provide external current. Figure 1The medium-power Mpower transistor uses PMOS to implement this function. However, PMOS naturally responds to load jumps more slowly than NMOS. Even though the FVF local loop improves this problem, the active loop still has bandwidth and slew rate limitations. For applications with large load currents, such as those greater than 1A, the required chip area and power consumption will increase dramatically.

[0007] Therefore, how to balance fast response, high-precision voltage regulation, wide adjustment range and good anti-interference ability under large load current conditions has become the core challenge facing linear regulator design. Summary of the Invention

[0008] The purpose of the present invention is to address the problems of large DC error and poor load regulation in traditional LDO structures, which require additional compensation for high loop gain to suppress the problem. A transimpedance flip-flop voltage follower drive linear regulator is proposed, which can quickly respond to large load current jumps, while having high DC accuracy, load regulation and high power supply rejection ratio, and also has a wider output voltage range.

[0009] The technical solution of the present invention is: The present invention provides a transimpedance flip voltage follower driving linear regulator, comprising a control module and a transimpedance flip voltage follower (TIFVF) module, wherein; The control module includes an error amplifier and a voltage-current converter connected in series, the inverting terminal of the error amplifier is connected to the output terminal Vout of the TIFVF module, a compensation network is provided between the error amplifier and the voltage-current converter, and the voltage-current converter outputs a current signal Ictrl as a control signal connected to the control signal input terminal of the TIFVF module; The control signal input terminal of the TIFVF module is connected to the current control signal Ictrl output by the voltage-to-current converter; the power supply terminal of the TIFVF module is connected to the input voltage Vin, Vin is an independent input source or is connected to the power supply VDD; the output terminal of the TIFVF module is connected to the load and is also connected to the inverting input of the error amplifier in the control module as a feedback signal; The inverting input terminal of the error amplifier obtains the output voltage Vout of the TIFVF module and compares it with the inverting terminal reference voltage Vref to generate an error signal. The error signal is amplified and processed by the compensation network to generate a control voltage signal Vctrl. The control voltage signal Vctrl is converted into a current control signal Ictrl after passing through a voltage-to-current converter. The current control signal Ictrl is input to the TIFVF module to adjust the output voltage Vout, forming a negative feedback loop.

[0010] Furthermore, the TIFVF module includes: A DC bias circuit includes an equivalent resistor Req, transistors Mp1 and Mp2, and current sources Ibias1 and Ibias2. The source of transistor Mp2 is connected to a current control signal Ictrl and a power supply VDD, the drain is connected in series with the current source Ibias1 and then to ground, and the gate is connected to the gate of transistor Mp1. The drain of transistor Mp1 is connected in series with the current source Ibias2 and then to ground. One end of the equivalent resistor Req is connected to the source of transistor Mp2, and the other end is connected to the output terminal Vout. The TIFVF receives the current control signal Ictrl as input, performs a DC operating point bias through a DC bias circuit, and decouples the bias relationship between the control voltage signal Vctrl and the output voltage Vout established by the transistor Mn1; A local negative feedback loop includes transistors Mp1, Mn1, Mp3, and a capacitor C. The source of transistor Mp3 is connected to a power supply VDD, and the drain is connected to the source of transistor Mp1. The connection point between transistors Mp3 and Mp1 is connected to the gate of a power transistor Mpower. The source of the power transistor Mpower serves as an output terminal Vout, and the drain is connected to an input voltage Vin. The connection point between the gate and source of transistor Mp3 is connected to one end of capacitor C, and the other end of capacitor C is connected to the power supply VDD. Both ends of capacitor C are connected in parallel to a current source Ibias1, and the output of current source Ibias1 is connected to the drain of transistor Mn1. The source of transistor Mn1 is connected in series with a current source Ibias2 and then to ground. The negative feedback loop forms a local negative feedback through transistors Mp1, Mn1 and Mp3 to reduce the equivalent resistance of the gate node of the power tube Mpower; The TIFVF module generates an output voltage Vout according to the current control signal Ictrl, and the output voltage Vout ranges from the ground potential to the input voltage Vin; the pole of the gate node of the power tube Mpower is pushed to a high frequency, thereby improving the response speed and the power supply rejection ratio.

[0011] Furthermore, the DC bias circuit performs the following steps: A reference voltage is established through the equivalent resistor Req to stabilize the working state of the transistor Mp2; Providing a static operating current to transistor Mp2 through current source Ibias1 to determine the on-threshold of transistor Mp2; Providing a static operating current to transistor Mp1 through current source Ibias2; A current mirror relationship is established between the transistors Mp1 and Mp2 to eliminate the direct influence of the control voltage signal Vctrl on the output voltage Vout.

[0012] Furthermore, the local negative feedback loop performs the following steps: The gate of transistor Mp1 is used as the input stage to receive the voltage signal converted by transistor Mp2 from the current control signal Ictrl. After passing through the local negative feedback loop formed by transistors Mp1-Mn1-Mp3, the source level of transistor Mp1 will follow the change of the source level of transistor Mp2. For this local negative feedback loop, the source of transistor Mp1 serves as the loop input stage. The voltage signal is converted into a current signal after passing through transistor Mp1. After passing through the drain of transistor Mp1 and the source of transistor Mn1, the amplified voltage signal is obtained at the drain of transistor Mn1 through the small-signal equivalent resistance of the drain node. The amplified voltage signal is transmitted to the gate of transistor Mp3, and then converted into a current by transistor Mp3. The current flows out from the drain of transistor Mp3 and is converted into a voltage signal again through the small-signal equivalent resistance of the drain node, which is the output stage of the local negative feedback loop. After the local negative feedback loop forms a closed loop, the impedance transformation effect of the negative feedback loop will reduce the small signal equivalent resistance of the gate node of the power tube Mpower, so that the low-frequency pole is transferred to the high-frequency band.

[0013] Furthermore, the transistors Mp1, Mp2, and Mp3 are PMOS transistors, and the transistor Mn1 and the power tube Mpower are NMOS transistors; or the transistors Mp1, Mp2, and Mp3 are NMOS transistors, and the transistor Mn1 and the power tube Mpower are PMOS transistors.

[0014] Furthermore, a voltage divider circuit is provided between the inverting end of the error amplifier and the output end Vout of the TIFVF module; the voltage divider circuit includes two series resistors, one end of the series resistor is connected to the output end Vout, and the other end is grounded. The connection point of the series resistors serves as the output of the voltage divider circuit, generating a feedback voltage Vfb that is output to the inverting input end of the error amplifier.

[0015] Furthermore, in the voltage divider circuit, the upper resistor is connected in parallel with the capacitor to improve the power supply rejection ratio.

[0016] Furthermore, the compensation network includes a series resistor-capacitor branch or a parallel resistor-capacitor branch, one end of the series resistor-capacitor branch or the parallel resistor-capacitor branch is connected to the control voltage signal Vctrl, and the other end is grounded.

[0017] Furthermore, the load is equivalent to a parallel circuit of a capacitor and a resistive load, or a parallel circuit of a capacitor and a constant current source load.

[0018] Furthermore, the error amplifier is composed of a transconductance amplifier OTA, or an operational amplifier OPA.

[0019] Beneficial effects of the present invention: The present invention discloses a linear voltage regulator suitable for large load current application scenarios. It adopts a transimpedance flip voltage follower structure and improves the response speed through NMOS transistors and a local negative feedback loop; introduces a control current signal as input, decouples the limiting relationship between the output voltage and the control voltage, and achieves a wide output voltage range; stabilizes the DC operating point by configuring an equivalent resistor and a bias current source, ensuring that the output voltage covers the full range.

[0020] The present invention forms an overall negative feedback loop through an error amplifier and a feedback network, improves the power supply rejection ratio through a voltage divider resistor device and a parallel capacitor; and optimizes loop stability and transient response through a compensation network.

[0021] The present invention achieves fast response, high DC accuracy and wide output voltage range under large load current through innovative structural design and control method, effectively solving the performance bottleneck problem of traditional linear regulators in such applications.

[0022] Other features and advantages of the present invention will be described in detail in the following detailed description. BRIEF DESCRIPTION OF THE DRAWINGS

[0023] The above and other objects, features and advantages of the present invention will become more apparent through a more detailed description of exemplary embodiments of the present invention with reference to the accompanying drawings, wherein like reference numerals generally represent like components throughout the exemplary embodiments of the present invention.

[0024] Figure 1 The core circuit diagram of the FVF module in the background technology is shown.

[0025] Figure 2 The system architecture diagram of the transimpedance flip voltage follower drive linear regulator of the present invention is shown.

[0026] Figure 3 Shown is the circuit diagram of the TIFVF module in the present invention.

[0027] Figure 4 The voltage divider circuit diagram of the present invention is shown.

[0028] Figure 5 The figure shows the compensation network circuit diagram of the present invention.

[0029] Figure 6 Shown is a load circuit diagram of the present invention.

[0030] Figure 7 The circuit diagram of the error amplifier in the present invention is shown.

[0031] Figure 8 The circuit diagram of the voltage-to-current converter in the present invention is shown. DETAILED DESCRIPTION

[0032] The preferred embodiments of the present invention will be described in more detail below with reference to the accompanying drawings. Although the preferred embodiments of the present invention are shown in the accompanying drawings, it should be understood that the present invention can be implemented in various forms and should not be limited to the embodiments set forth herein.

[0033] Figure 2 The system architecture diagram of the transimpedance flip voltage follower drive linear regulator of the present invention is shown.

[0034] like Figure 2 As shown, the present invention provides a transimpedance flip voltage follower driving linear regulator, including a control module and a transimpedance flip voltage follower, namely a TIFVF module, wherein; The control module includes an error amplifier and a voltage-current converter connected in series, the inverting terminal of the error amplifier is connected to the output terminal Vout of the TIFVF module, a compensation network is provided between the error amplifier and the voltage-current converter, and the voltage-current converter outputs a current signal Ictrl as a control signal connected to the control signal input terminal of the TIFVF module; The control signal input terminal of the TIFVF module is connected to the current control signal Ictrl output by the voltage-to-current converter; the power supply terminal of the TIFVF module is connected to the input voltage Vin, Vin is an independent input source or is connected to the power supply VDD; the output terminal of the TIFVF module is connected to the load and is also connected to the inverting input of the error amplifier in the control module as a feedback signal; The inverting input terminal of the error amplifier obtains the output voltage Vout of the TIFVF module and compares it with the inverting terminal reference voltage Vref to generate an error signal. The error signal is amplified and processed by the compensation network to generate a control voltage signal Vctrl. The control voltage signal Vctrl is converted into a current control signal Ictrl after passing through a voltage-to-current converter. The current control signal Ictrl is input to the TIFVF module to adjust the output voltage Vout, forming a negative feedback loop.

[0035] In this embodiment, the output voltage VOUT is fed back to the error amplifier and compared with the reference voltage VREF to generate an error signal. This signal is then amplified and conditioned by the compensation network to produce the control voltage signal VCTRL. VCTRL then passes through a voltage-to-current conversion circuit to generate the current control signal ICTRL required by TIFVF. This constitutes a negative feedback loop, in which the error amplifier and voltage-to-current conversion stages provide sufficient loop gain.

[0036] like Figure 3 As shown, the TIFVF module includes: A DC bias circuit includes an equivalent resistor Req, transistors Mp1 and Mp2, and current sources Ibias1 and Ibias2. The source of transistor Mp2 is connected to a current control signal Ictrl and a power supply VDD, the drain is connected in series with the current source Ibias1 and then to ground, and the gate is connected to the gate of transistor Mp1. The drain of transistor Mp1 is connected in series with the current source Ibias2 and then to ground. One end of the equivalent resistor Req is connected to the source of transistor Mp2, and the other end is connected to the output terminal Vout. The TIFVF receives the current control signal Ictrl as input, performs a DC operating point bias through a DC bias circuit, and decouples the bias relationship between the control voltage signal Vctrl and the output voltage Vout established by the transistor Mn1; A local negative feedback loop includes transistors Mp1, Mn1, Mp3, and a capacitor C. The source of transistor Mp3 is connected to a power supply VDD, and the drain is connected to the source of transistor Mp1. The connection point between transistors Mp3 and Mp1 is connected to the gate of a power transistor Mpower. The source of the power transistor Mpower serves as an output terminal Vout, and the drain is connected to an input voltage Vin. The connection point between the gate and source of transistor Mp3 is connected to one end of capacitor C, and the other end of capacitor C is connected to the power supply VDD. Both ends of capacitor C are connected in parallel to a current source Ibias1, and the output of current source Ibias1 is connected to the drain of transistor Mn1. The source of transistor Mn1 is connected in series with a current source Ibias2 and then to ground. The negative feedback loop forms a local negative feedback through transistors Mp1, Mn1 and Mp3 to reduce the equivalent resistance of the gate node of the power tube Mpower; The TIFVF module generates an output voltage Vout according to the current control signal Ictrl, and the output voltage Vout ranges from the ground potential to the input voltage Vin; the pole of the gate node of the power tube Mpower is pushed to a high frequency, thereby improving the response speed and the power supply rejection ratio.

[0037] In one example, the DC bias circuit performs the following steps: A reference voltage is established through the equivalent resistor Req to stabilize the working state of the transistor Mp2; Providing a static operating current to transistor Mp2 through current source Ibias1 to determine the on-threshold of transistor Mp2; Providing a static operating current to transistor Mp1 through current source Ibias2; A current mirror relationship is established between the transistors Mp1 and Mp2 to eliminate the direct influence of the control voltage signal Vctrl on the output voltage Vout.

[0038] In this embodiment, a control current signal is introduced as input from a transimpedance flip voltage follower structure. The control current signal is generated by a voltage-current conversion circuit and cooperates with a DC bias circuit to decouple the limiting relationship between the output voltage and the control voltage. For the control current signal, an equivalent resistor and a bias current source are configured. The configuration is used to stabilize the DC operating point and ensure that the output voltage range covers the full range from the ground voltage to the input voltage. The DC operating point bias makes the output voltage Vout no longer affected by the Figure 1 The gate-source voltage of transistor Mp1 is limited.

[0039] In one example, the local negative feedback loop performs the following steps: The gate of transistor Mp1 is used as the input stage to receive the voltage signal converted by transistor Mp2 from the current control signal Ictrl. After passing through the local negative feedback loop formed by transistors Mp1-Mn1-Mp3, the source level of transistor Mp1 will follow the change of the source level of transistor Mp2. For this local negative feedback loop, the source of transistor Mp1 serves as the loop input stage. The voltage signal is converted into a current signal after passing through transistor Mp1. After passing through the drain of transistor Mp1 and the source of transistor Mn1, the amplified voltage signal is obtained at the drain of transistor Mn1 through the small-signal equivalent resistance of the drain node. The amplified voltage signal is transmitted to the gate of transistor Mp3, and then converted into a current by transistor Mp3. The current flows out from the drain of transistor Mp3 and is converted into a voltage signal again through the small-signal equivalent resistance of the drain node, which is the output stage of the local negative feedback loop. After the local negative feedback loop forms a closed loop, the impedance transformation effect of the negative feedback loop will reduce the small signal equivalent resistance of the gate node of the power tube Mpower, so that the low-frequency pole is transferred to the high-frequency band.

[0040] In this embodiment, a local negative feedback loop is constructed by a loop structure composed of multiple transistors; the equivalent resistance value of the output node is reduced by the local negative feedback loop; according to the feedback characteristics of the local negative feedback loop, the stability of the output voltage is adjusted, and a rapid response is made to changes in the load current; through the configuration of the local negative feedback loop, the DC accuracy of the circuit is optimized, and the load regulation rate of the overall circuit is improved.

[0041] In the present invention, the transistors Mp1, Mp2, and Mp3 are PMOS transistors; the transistors Mn1 and Mpower are NMOS transistors; or the transistors Mp1, Mp2, and Mp3 are NMOS transistors; the transistors Mn1 and Mpower are PMOS transistors.

[0042] In one example, if Figure 4The figure shows a voltage divider circuit diagram of the present invention; a voltage divider circuit is provided between the inverting end of the error amplifier and the output end Vout of the TIFVF module; the voltage divider circuit includes two series resistors, one end of the series resistor is connected to the output end Vout, and the other end is grounded. The connection point of the series resistors serves as the output of the voltage divider circuit, generating a feedback voltage Vfb that is output to the inverting input end of the error amplifier; in the voltage divider circuit, a capacitor is connected in parallel with the upper resistor to improve the power supply rejection ratio.

[0043] In this embodiment, the voltage divider circuit divides the output voltage to generate a feedback voltage, and improves the power supply rejection ratio through a parallel capacitor.

[0044] In one example, if Figure 5 The compensation network circuit diagram of the present invention is shown; the compensation network includes a series resistor-capacitor branch or a parallel resistor-capacitor branch, one end of the series resistor-capacitor branch or the parallel resistor-capacitor branch is connected to the control voltage signal Vctrl, and the other end is grounded.

[0045] In this embodiment, the parameters of the compensation network are adjusted according to the output characteristics of the transimpedance flip-over voltage follower structure. The compensation network is composed of a combination of resistors and capacitors and is used to optimize loop stability and transient response.

[0046] In one example, Figure 6 The load circuit diagram of the present invention is shown, and the load is equivalent to a parallel circuit of a capacitor and a resistive load, or a parallel circuit of a capacitor and a constant current source load.

[0047] In this embodiment, an equivalent circuit including a capacitor and a resistive load is constructed for the load model of the linear regulator to simulate an actual load jump scenario and verify the dynamic response performance of the regulator.

[0048] In one example, Figure 7 The circuit diagram of the error amplifier in the present invention is shown. The error amplifier is composed of a transconductance amplifier OTA or an operational amplifier OPA.

[0049] While various embodiments of the present invention have been described above, the above description is intended to be illustrative, not exhaustive, and not limited to the disclosed embodiments. Many modifications and variations will be apparent to those skilled in the art without departing from the scope and spirit of the described embodiments.

Claims

1. A transimpedance flip voltage follower drive linear regulator, characterized in that It includes a control module and a transimpedance flip voltage follower, namely a TIFVF module, wherein; The control module includes an error amplifier and a voltage-current converter connected in series, the inverting terminal of the error amplifier is connected to the output terminal Vout of the TIFVF module, a compensation network is provided between the error amplifier and the voltage-current converter, and the voltage-current converter outputs a current signal Ictrl as a control signal connected to the control signal input terminal of the TIFVF module; The control signal input terminal of the TIFVF module is connected to the current control signal Ictrl output by the voltage-to-current converter; the power supply terminal of the TIFVF module is connected to the input voltage Vin, Vin is an independent input source or is connected to the power supply VDD; the output terminal of the TIFVF module is connected to the load and is also connected to the inverting input of the error amplifier in the control module as a feedback signal; The inverting input terminal of the error amplifier obtains the output voltage Vout of the TIFVF module and compares it with the inverting terminal reference voltage Vref to generate an error signal. The error signal is amplified and processed by the compensation network to generate a control voltage signal Vctrl. The control voltage signal Vctrl is converted into a current control signal Ictrl after passing through a voltage-to-current converter. The current control signal Ictrl is input to the TIFVF module to adjust the output voltage Vout, forming a negative feedback loop.

2. The transimpedance flip voltage follower drive linear regulator according to claim 1, characterized in that The TIFVF module includes: A DC bias circuit includes an equivalent resistor Req, transistors Mp1 and Mp2, and current sources Ibias1 and Ibias2. The source of transistor Mp2 is connected to a current control signal Ictrl and a power supply VDD, the drain is connected in series with the current source Ibias1 and then to ground, and the gate is connected to the gate of transistor Mp1. The drain of transistor Mp1 is connected in series with the current source Ibias2 and then to ground. One end of the equivalent resistor Req is connected to the source of transistor Mp2, and the other end is connected to the output terminal Vout. The TIFVF receives the current control signal Ictrl as input, performs a DC operating point bias through a DC bias circuit, and decouples the bias relationship between the control voltage signal Vctrl and the output voltage Vout established by the transistor Mn1; A local negative feedback loop includes transistors Mp1, Mn1, Mp3, and a capacitor C. The source of transistor Mp3 is connected to a power supply VDD, and the drain is connected to the source of transistor Mp1. The connection point between transistors Mp3 and Mp1 is connected to the gate of a power transistor Mpower. The source of the power transistor Mpower serves as an output terminal Vout, and the drain is connected to an input voltage Vin. The connection point between the gate and source of transistor Mp3 is connected to one end of capacitor C, and the other end of capacitor C is connected to the power supply VDD. Both ends of capacitor C are connected in parallel to a current source Ibias1, and the output of current source Ibias1 is connected to the drain of transistor Mn1. The source of transistor Mn1 is connected in series with a current source Ibias2 and then to ground. The negative feedback loop forms a local negative feedback through transistors Mp1, Mn1 and Mp3 to reduce the equivalent resistance of the gate node of the power tube Mpower; The TIFVF module generates an output voltage Vout according to the current control signal Ictrl, and the output voltage Vout ranges from the ground potential to the input voltage Vin; the pole of the gate node of the power tube Mpower is pushed to a high frequency, thereby improving the response speed and the power supply rejection ratio.

3. The transimpedance flip voltage follower drive linear regulator according to claim 2, characterized in that The DC bias circuit performs the following steps: A reference voltage is established through the equivalent resistor Req to stabilize the working state of the transistor Mp2; Providing a static operating current to transistor Mp2 through current source Ibias1 to determine the on-threshold of transistor Mp2; Providing a static operating current to transistor Mp1 through current source Ibias2; A current mirror relationship is established between the transistors Mp1 and Mp2 to eliminate the direct influence of the control voltage signal Vctrl on the output voltage Vout.

4. The transimpedance flip voltage follower drive linear regulator according to claim 2, characterized in that The local negative feedback loop performs the following steps: The gate of transistor Mp1 is used as the input stage to receive the voltage signal converted by transistor Mp2 from the current control signal Ictrl. After passing through the local negative feedback loop formed by transistors Mp1-Mn1-Mp3, the source level of transistor Mp1 will follow the change of the source level of transistor Mp2. For this local negative feedback loop, the source of transistor Mp1 serves as the loop input stage. The voltage signal is converted into a current signal after passing through transistor Mp1. After passing through the drain of transistor Mp1 and the source of transistor Mn1, the amplified voltage signal is obtained at the drain of transistor Mn1 through the small-signal equivalent resistance of the drain node. The amplified voltage signal is transmitted to the gate of transistor Mp3, and then converted into a current by transistor Mp3. The current flows out from the drain of transistor Mp3 and is converted into a voltage signal again through the small-signal equivalent resistance of the drain node, which is the output stage of the local negative feedback loop. After the local negative feedback loop forms a closed loop, the impedance transformation effect of the negative feedback loop will reduce the small signal equivalent resistance of the gate node of the power tube Mpower, so that the low-frequency pole is transferred to the high-frequency band.

5. The transimpedance flip voltage follower drive linear regulator according to claim 2, characterized in that The transistors Mp1, Mp2, and Mp3 are PMOS transistors, and the transistor Mn1 and the power tube Mpower are NMOS transistors; or the transistors Mp1, Mp2, and Mp3 are NMOS transistors, and the transistor Mn1 and the power tube Mpower are PMOS transistors.

6. The transimpedance flip voltage follower drive linear regulator according to claim 1, characterized in that A voltage divider circuit is provided between the inverting end of the error amplifier and the output end Vout of the TIFVF module; the voltage divider circuit includes two series resistors, one end of the series resistor is connected to the output end Vout, and the other end is grounded. The connection point of the series resistors serves as the output of the voltage divider circuit, generating a feedback voltage Vfb that is output to the inverting input end of the error amplifier.

7. The transimpedance flip voltage follower drive linear regulator according to claim 6, characterized in that In the voltage divider circuit, the upper resistor is connected in parallel with the capacitor to improve the power supply rejection ratio.

8. The transimpedance flip voltage follower drive linear regulator according to claim 1, characterized in that The compensation network includes a series resistor-capacitor branch or a parallel resistor-capacitor branch, one end of the series resistor-capacitor branch or the parallel resistor-capacitor branch is connected to the control voltage signal Vctrl, and the other end is grounded.

9. The transimpedance flip voltage follower drive linear regulator according to claim 1, characterized in that The load is equivalent to a parallel circuit of a capacitor and a resistive load, or a parallel circuit of a capacitor and a constant current source load.

10. The transimpedance flip voltage follower drive linear regulator according to claim 1, characterized in that The error amplifier is composed of a transconductance amplifier OTA or an operational amplifier OPA.

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