Joint sensing method for orthogonal frequency domain multiplexing communication system and related user equipment

Abstract

A joint perception method for an Orthogonal Frequency Division Multiplexing (OFDM) communication system includes: transmitting a plurality of Reference Signal (RS) Resource Elements (REs) from a set of interleaved comb patterns to a perception terminal; and determining the plurality of RS resource units to perform complete cycle interleaving, partial cycle interleaving, or a combination of complete cycle and partial cycle interleaving.

Description

[0001] Cross-references to related applications

[0002] This application claims the benefit of U.S. Provisional Application No. 63 / 490,017, filed March 14, 2023, the contents of which are incorporated herein by reference. Technical Field

[0003] This invention relates to a joint sensing method and related user equipment for an orthogonal frequency domain multiplexing communication system, and more specifically, to a joint sensing method and related user equipment for an orthogonal frequency domain multiplexing communication system that can improve the efficiency of radio resources. Background Technology

[0004] When Orthogonal Frequency Domain Multiplexing (OFDM) is applied to joint communication and sensing, the configuration of the reference signal is crucial to conventional sensing performance, especially for bistatic sensing. However, the ambiguity characteristics in the delay (i.e., range) and Doppler frequency (i.e., velocity) domains differ depending on the reference signal pattern. Furthermore, current localization reference signals (PRS) are designed for single-target localization using conventional IFFT algorithms. Summary of the Invention

[0005] In view of this, the present invention provides a joint sensing method and related user equipment (UE) for orthogonal frequency domain multiplexing (OFDM) communication systems to improve the ambiguity function characteristics related to RS patterns and algorithms, and utilizes comb-shaped sensing reference signal patterns and super-resolution sensing algorithms based on full-cycle interleaving and partial-cycle interleaving.

[0006] One embodiment of the present invention provides a joint sensing method for an orthogonal frequency domain multiplexing (OFDM) communication system, comprising: transmitting a plurality of reference signal (RS) resource elements (REs) from a set of interleaved comb patterns to a sensing terminal; and determining the plurality of RS resource elements to perform full-cycle interleaving, partial-cycle interleaving, or a combination of full-cycle and partial-cycle interleaving.

[0007] Another embodiment of the present invention provides a user equipment (UE) for an orthogonal frequency domain multiplexing (OFDM) communication system, comprising: a radio transceiver configured to perform radio transmission and reception with a serving terminal; and a controller configured to determine a plurality of RS resource elements to perform full-cycle interleaving, partial-cycle interleaving, or a combination of full-cycle and partial-cycle interleaving.

[0008] These and other objectives of the present invention will become apparent to those skilled in the art upon reading the following detailed description of preferred embodiments, which are illustrated in the various figures and drawings. Attached Figure Description

[0009] Figure 1 This is a schematic diagram of a wireless communication network according to an embodiment of the present invention.

[0010] Figures 2A, 2B, and 2C are schematic diagrams of different interlaced offset patterns of the comb-like structure according to embodiments of the present invention.

[0011] Figure 3 This is a schematic diagram of the comb-like structure of the RS pattern according to an embodiment of the present invention.

[0012] Figure 4 This is a schematic diagram illustrating different snapshot examples of comb-based RS symbols in the absence of interleaving, according to embodiments of the present invention.

[0013] Figure 5 This is a schematic diagram illustrating an example of a fuzzy function for 2D MUSIC according to an embodiment of the present invention.

[0014] Figure 6 This is a schematic diagram of an example of a comb-based RS symbol snapshot according to an embodiment of the present invention.

[0015] Figures 7A and 7B are schematic diagrams of examples of fuzzy functions according to embodiments of the present invention.

[0016] Figures 8A and 8B are schematic diagrams of examples of fuzzy functions according to embodiments of the present invention.

[0017] Figure 9 This is a schematic diagram of an example of a comb-based RS symbol snapshot according to an embodiment of the present invention.

[0018] Figures 10A and 10B are schematic diagrams illustrating examples of fuzzy functions using 2D MUSIC according to embodiments of the present invention.

[0019] Figures 11A and 11B are schematic diagrams illustrating examples of fuzzy functions using IAA according to embodiments of the present invention.

[0020] Figures 12A, 12B, 12C, and 12D are schematic diagrams of the comb-like structure of a reference signal (RS) pattern according to an embodiment of the present invention.

[0021] Figures 13A, 13B, and 13C are schematic diagrams illustrating examples of fuzzy characteristics under a zero-delay target with different interleaving sequences according to embodiments of the present invention.

[0022] Figure 14 This is a schematic diagram illustrating different snapshot examples of comb-based RS symbols in the absence of interleaving, according to embodiments of the present invention.

[0023] Figures 15A, 15B, and 15C are schematic diagrams illustrating the fuzzy characteristics of the interleaved sequence under a zero-delay target according to an embodiment of the present invention.

[0024] Figures 16A, 16B, and 16C are schematic diagrams of the results of three targets having an interlaced sequence and a comb-4 structure according to an embodiment of the present invention. Detailed Implementation

[0025] Figure 1 This is a schematic diagram of a wireless communication network 100 according to an embodiment of the present invention.

[0026] like Figure 1 As shown, the wireless communication network 100 may include a user equipment (UE) 110 and a service network 120, wherein the UE 110 may wirelessly connect to the service network 120 to obtain mobile services and perform cell measurements on one or more cells of the service network 120.

[0027] UE 110 can be a feature phone, smartphone, tablet PC, laptop, mobile vehicle, or any wireless communication device using wireless technologies (such as 5G NR technology) that support the service network 120. In another embodiment, UE 110 can support multiple wireless technologies. For example, the UE can support 5G NR technology and traditional 4G technologies such as LTE / LTE-A / TD-LTE.

[0028] The service network 120 includes an access network 121 and a core network 122. The access network 121 is responsible for processing radio signals, terminating radio protocols, and connecting the UE 110 to the core network 122. The core network 122 is responsible for performing mobility management, network-side authentication, and interfacing with public / external networks (e.g., the Internet). Each of the access network 121 and the core network 122 may include one or more network nodes to perform the above functions.

[0029] In one embodiment, the serving network 120 may be a 5G NR network, the access network 121 may be a radio access network (RAN), and the core network 122 may be a next-generation core network (NG-CN).

[0030] The RAN can include one or more cellular sites, such as next-generation node Bs (gNBs) supporting high-frequency bands (e.g., above 24 GHz). Each gNB can further include one or more transport receiver points (TRPs), where each gNB or TRP can be referred to as a 5G cellular site. Some gNB functions can be distributed across different TRPs, while other functions can be centralized to meet the needs of specific situations.

[0031] A 5G cellular base station can form one or more cells with different component carriers (CCs) to provide mobile services to UE 110. For example, UE 110 can camp on one or more cells formed by one or more gNBs or TRPs, where the cell camped by UE 110 can be referred to as the serving cell, which includes a primary cell (Pcell) and one or more secondary cells (Scells).

[0032] NG-CN typically consists of various network functions, including Access and Mobility Functions (AMF), Session Management Functions (SMF), Policy Control Functions (PCF), Application Functions (AF), Authentication Server Functions (AUSF), User Plane Functions (UPF), and User Data Management (UDM). Each of these network functions can be implemented as a network element on dedicated hardware, run as a software instance on dedicated hardware, or be a virtualized function instantiated on a suitable platform (e.g., cloud infrastructure).

[0033] The AMF provides UE-based authentication, authorization, and mobility management. The SMF is responsible for session management and assigning Internet Protocol (IP) addresses to the UE. It also selects and controls the UPF for data transmission. If a UE has multiple sessions, a different SMF may be assigned to each session to manage them individually, and different functions may be provided for each session. The AF provides packet flow information to the PCF, which is responsible for policy control, to support Quality of Service (QoS). Based on the information, the PCF determines policies regarding mobility and session management to ensure the proper functioning of the AMF and SMF. The AUSF stores data used for UE authentication, while the UDM stores the UE's subscription data.

[0034] In another embodiment, the serving network 120 may be an LTE / LTE-A / TD-LTE network, the access network 121 may be an evolved Universal Terrestrial Radio Access Network (E-UTRAN), and the core network 122 may be an evolved Packet Core (EPC).

[0035] E-UTRAN may include at least one cellular site, such as an evolved Node B (eNB) (e.g., macro eNB, micro eNB, or pico eNB), each eNB may form a cell to provide mobile services to UE 110. For example, UE 110 may camp on one or more cells formed by one or more eNBs, where the cell camped by UE 110 may be referred to as the serving cell, containing one Pcell and one or more Scells.

[0036] EPC may include a Home User Server (HSS), a Mobility Management Entity (MME), a Serving Gateway (S-GW), and a Packet Data Network Gateway (PDN-GW or P-GW).

[0037] It should be understood that Figure 1 The wireless communication network 100 described herein is for illustrative purposes and is not intended to limit the scope of application. For example, the wireless communication network 100 may include a 5G NR network and a legacy network (such as an LTE / LTE-A / TD-LTE network or a WCDMA network), and the UE 110 may wirelessly connect to the 5G NR network and the legacy network.

[0038] One embodiment of the present invention derives a standard for selecting reference signal patterns for super-resolution sensing algorithms, improves the fuzzy function characteristics associated with such RS pattern and algorithm selection, and applies the derived principles to new 6G joint communication sensing or to improve existing 5G NR and RS patterns.

[0039] Please refer to Figures 2(a), 2(b), and 2(c), which are schematic diagrams of different interleaved offset patterns of the comb structure according to an embodiment of the present invention. As shown in Figures 2(a), 2(b), and 2(c), the comb structure, namely Comb-4, is used to support scenarios requiring high dynamic range. Matched filters and frequency bins can be applied to the configurations of Figures 2(a) and 2(b) to enable the scheme to support an extended 2D unambiguous range.

[0040] On the other hand, the configuration shown in Figure 2(c) can extend the 2D unambiguous range of delay and Doppler by removing some of the lower-power sidepeaks, but this sacrifices the perceptual dynamic range of the detectable target signal strength. Furthermore, super-resolution algorithms such as Multi-Signal Classification (MUSIC) and iterative adaptive methods may exhibit better unambiguous range in the case of Figure 2(c).

[0041] like Figure 3 As shown, let S sub (Unit: subcarrier number) represents the spacing of RS resource elements (REs) in the frequency domain, S sub ≥2 indicates a comb-like structure, S sym (Unit: symbol number) indicates the spacing between RS symbols in the time domain. The current positioning reference signal (PRS) uses S... sym =1,F i (Unit: subcarrier number) represents the interleaving offset of the i-th RS symbol in the frequency domain, T s T represents the duration of OFDM. cp The duration of the cyclic prefix (CP) is represented by T = T cp +T s Indicates the duration of the OFDM symbol with added CP. The RS pattern can be represented by S. sub ,S sym and F iAdjustments will be made.

[0042] RS patterns can be obtained through S sub ,S sym and F i Adjustments are made. For matched filters with frequency binning and 2DFFT, interleaving with different interleaving offsets for different RS symbols can eliminate some time delay ambiguities in the 2D range. Define mod(Z,M)∈{0,1,..M-1}, for any integers Z and M, where mod is the modulo operation. The following are two interleaving formats:

[0043] Interleaving scheme A: Interleaving offset satisfies F i =mod(p·i+β1,S) sub ), where p and S sub and β1∈{0,1,…S sub -1}, i=0,1,.... are coprime.

[0044] Interleaving scheme B: Interleaving offsets satisfy the condition that no integer pairs exist. Make the following system of modular arithmetic equations hold true.

[0045] mod(lk2-(F l -F0)κ1,S sub ) = 0, for l = 1, 2, ..., i sym U F -1,

[0046] in U represents the number of times a specific interlaced pattern is repeated in a snapshot. F It represents the number of symbols within a specific interlaced pattern, l represents the duration of the signal in a snapshot, and Typically, when the number of equations i sym U F When less than or equal to 2, the inverse condition can be satisfied by κ2=(F1-f0)κ1. Therefore, i is required. sym U F ≥3 to ensure that the system of equations has no solution.

[0047] One implementation is that when S sub When the number is even and greater than 2, use PRS(U) F =S sub The same alternation order, and

[0048] Where β2 is an integer ∈ {0,1,2,…S} sub -1}.

[0049] When S sub When F0 = 2, one embodiment is F0 = 0, F1 = 1, F2 = 1, F3 = 0 and UF =4,i sym =1.

[0050] The following describes the RS configurations for different super-resolution sensing algorithms.

[0051] MUSIC (Multi-Signal Classification):

[0052] MUSIC is a super-resolution sensing algorithm, but it requires multiple snapshots and exhibits relatively high complexity. 2DMUSIC is used for comb structures in the frequency domain, such as... Figure 4 , Figure 6 and Figure 9 As shown. U sub and U sym These are used to determine the bandwidth used and the duration of each snapshot, respectively.

[0053]

[0054] U sym =i sym ·S sym ·U F

[0055] in U represents the number of times a specific interlaced pattern is repeated in a snapshot. F It is the number of symbols within a specific interlaced pattern.

[0056] Figure 4 This explains the selection of each snapshot for comb-based RS symbols without interleaving U. sub =2S Sub U sym =4S sym An example of this is where "spatial smoothing" is employed to avoid the rank deficiency problem. In this case, U F =1. The (m+1)th snapshot will be determined by mS at the symbol index. sym and on the subcarrier index by mS sub Offset relative to the 1st snapshot. For the (m+1)th snapshot, where m = 0, 1, 2, ..., (A) m =BS m +N m , where N m It's noise, (A) m S is the unmodulated non-zero RS REs sequence received in the m-th snapshot, B is the steering matrix to be estimated (which remains unchanged between snapshots), and S m It is the magnitude vector. Figure 4 In this case, the h-th column of the guidance matrix B can be written as:

[0057]

[0058] Where H+1 is the total number of targets, f h and τ h It represents the Doppler frequency and time delay of the h-th target.

[0059]

[0060] , where αi is the reflection coefficient of the i-th target, and m = 0, 1, 2, ...

[0061]

[0062] Observe the guidance matrix B, in In the case of τ and f, blurring will occur, where τ and f are the real delay and Doppler, and (k1,k2) are integer pairs. Figure 5 It shows that in the absence of intersecting S sym =1,S sub When =4, (0,0) is used as the blur function of the 2D MUSIC for the true delay and Doppler pair.

[0063] Figure 6 This illustrates the use of interleaved scheme A as a comb-based RS symbol (U sub =2S Sub U sym =S sub S sym (p=1, β1=0) Select an instance of each snapshot. Spatial smoothing is used to avoid the rank deficiency problem. In this case, U F =S sub The (m+1)th snapshot will be stored in the symbol index by mS. sym and in the subcarrier index Shift relative to the 1st snapshot, where This is a floor operation. For a fixed number of snapshots, this case requires less RE than other cases. For the (m+1)th snapshot, the h-th column B of the steering matrix is...

[0064]

[0065] , where h=0,1,…H.

[0066]

[0067] When using staggered scheme A, it can be concluded that ambiguity occurs and At this point, (k1, k2) are integer pairs, and τ and f are the true delay and Doppler. For example, when p = 1, it can be concluded that blurring occurs... At the given location, (k1,k2) are integer pairs, and τ and f are real delay and Doppler pairs.

[0068] Figure 7(a) , 7(b) Shown in S sym =1,S sub The fuzzy function of 2D MUSIC using the staggered scheme A is shown in Figure 7(a) for p=1 and Figure 7(b) for p=3.

[0069] Figure 8(a) , 8(b) Shown in S sym =1,S sub The fuzzy function of 2D MUSIC using the interleaved scheme A is shown in Figure 8(a) for p=3 and Figure 8(b) for p=5.

[0070] Figure 9 This demonstrates the use of interleaved scheme B for comb-based RS symbol U. sub =2S Sub ,u sym =S sub S sym U F =S sub Select an instance of each snapshot. Spatial smoothing is used to avoid the rank deficiency problem. In this case, U F This depends on the selection of the interleaving pattern in interleaving scheme B that satisfies the above conditions. Compared to the 1st snapshot, the (m+1)th snapshot will shift by mU in the symbol index. F S sym Shift mS on the subcarrier index sub Therefore, with a fixed number of snapshots, this case requires more REs than the other cases described above. For the (m+1)th snapshot, the h-th column of the steering matrix B is...

[0071]

[0072] , where h=0,1,…H.

[0073] Consider the matrix:

[0074]

[0075] Please note that matrix B may not be able to distinguish between (τ,f) and For integer pairs (k1, k2), the choice of interleaving offset is irrelevant. For interleaving scheme B, ambiguity only occurs in... This means from 0 to T sThere are no side peaks within the time delay range. The condition that side peaks do not exist is satisfied only if the following statement is true: there is no scalar τ′-τ∈(0,T) s )and This makes the following equation (hereinafter referred to as the "inverse condition") true.

[0076]

[0077] For all i = 0, 1, ..., i sub -1,l=0,1,…,i sym U F -1.

[0078] Note that the equation with the inverse condition above can be equivalently rewritten in the following form:

[0079]

[0080] Where κ′1 is any integer. Since the MUSIC algorithm is invariant to constant phase rotation, the interleaved sequence F... l Equivalent to F l +β2 for any Let F0 = 0 without loss of generality. Then, for l = 0, the inverse condition is: This produces Where κ1 is any integer. Based on the assumption τ′-τ∈(0,T) s ), which may have κ1∈{1,2,…,S sub -1}. Therefore, the interleaved sequence F l Equivalent to mod(F) l +β2,S sub And we can assume F l ∈{0,1,…,S sub -1} for any l.

[0081] Consider the inverse condition that l ≠ 0 in general. The equation requires... It is an integer, and It is an integer. Therefore, this condition is equivalent to lacking a solution (f′-f,κ1) to the system of equations.

[0082] mod(l·S sym S sub T(f′-f)-F l κ1,S sub ) = 0, for l = 1, 2, ..., i sym U F -1..

[0083] Please note that if a solution exists, the equation l = 1 implies the quantity S. sym S subT(f′-f) is an integer. We denote it as k2. When F0 = 0, the condition is ultimately rewritten as lacking a solution. To the equation system: mod(lκ2-F) l κ1,S sub ) = 0, for l = 1, 2, ..., i sym U F -1.

[0084] Typically, it is possible to deal with {F} i Applying constant phase rotation, the system of equations with the inverse condition becomes: mod(lκ2-(F) l -F0)κ1,S sub ) = 0, for l = 1, 2, ..., i sym U s -1.

[0085] When S sub When S is a prime number, the only case where the condition is not met is the aforementioned alternation scheme A. Otherwise, an ideal alternation scheme can be constructed based on the above conditions. For example, when S... sub When the number is even and greater than 2, one embodiment that satisfies this condition is to use the same interleaving order as PRS. Where β2 is an integer ∈ {0,1,2,S} sub -1}.

[0086] Typically, when the number of equations i sym U F When κ2 = (F1 - F0)κ1 is less than or equal to 2, the inverse condition can be satisfied. Therefore, i is required. sym U F ≥3 is used to ensure that there are no side peaks within the range.

[0087] Figure 10(a) , 10(b) Shown in S sym =1,S sub =4 and S sym =1,S sub In the case of 8, one embodiment of the interleaving scheme B is used, which employs the real delay of 2D MUSIC and the Doppler blur function of (0,0).

[0088] The results show that staggered scheme B and MUSIC provide the optimal 2D unambiguous range among all options. Depending on the application scenario, the maximum unambiguous 2D range (0,0) around the main peak may have different options, i.e., from 0 to T. s Time delay, I to The Doppler frequency, where I is a specified value and

[0089] IAA:

[0090] IAA is a super-resolution, mesh algorithm that requires only a single snapshot. Using a fixed number of REs, IAA can achieve better delay and Doppler resolution than MUSIC because it does not require "spatial smoothing" and multiple snapshots. The blur characteristics corresponding to different RS configurations in the delay and Doppler domains show the same results as MUSIC. It formulates the perception problem as V = WS + N, where...

[0091]

[0092] It is a vectorized reception of non-zero RS RE, without modulation. The signal bandwidth is determined by M, and the time duration is determined by M. The W column in column h can be written as

[0093]

[0094] Where h represents the h-th grid in the delay and Doppler domains, h = 0, 1, 2, ..., G, and G represents the grid density, with larger G values ​​resulting in a denser grid in the generated two-dimensional fuzzy function. It can be observed that matrix W in the IAA exhibits the same structure as matrix B in the MUSIC. Therefore, the conditions for the staggered scheme B proposed in the MUSIC section also apply to the IAA.

[0095] Figure 11(a) , 11(b) Shown in S sub =4,S sym Several instances of using the ambiguity function of IAA in the case of =1. Similarly, it can be concluded that the interleaved scheme B with IAA (Figure 11(b)) provides the optimal 2D unambiguous range among all options. Depending on the application scenario, the maximum unambiguous 2D range (0,0) around the main peak may have different options, i.e., from 0 to T_s time delay, I to... The Doppler frequency, where I is a specified value and

[0096] The above embodiments analyze radar perception to detect Doppler and time delay. The following are examples of multi-target localization using different algorithms in joint communications:

[0097] Traditional 5G NR positioning solutions do not consider using super-resolution algorithms such as MUSIC and IAA to adjust the RS pattern of the communication system to achieve the required ambiguity performance. This invention proposes a method for positioning or ranging using full-period interlaced and partially-period interlaced comb sensing reference signal patterns and super-resolution sensing algorithms.

[0098] Please see Figure 12(a) , 12(b) 12(c) and 12(d) are schematic diagrams of the RS pattern comb structure according to embodiments of the present invention. The RS pattern includes a plurality of RS resource units (REs).

[0099] One embodiment uses a full periodic interleaving arrangement of the comb structure and a partial periodic interleaving arrangement within the comb structure (i.e., comb-4), such as Figure 12(a) , 12(b) As shown in 12(c) and 12(d), this may eliminate the range [0,T] s The side peak of ) where T S This is the OFDM symbol duration. Define mgo(Z,M)∈{0,1,..M-1} for any integers Z and M, where mod is the modulo operation, and S... sub It is a comb-like density.

[0100] Overall, Figure 12(a) , 12(b) The alternation order in 12(c) is an example of a partially periodic alternation scheme: (mod(β1,S) sub ),mod(β1+1,S sub ), where β1=0,1,…,S sub -1, they are subsets of the alternating order (mod(β,S)). sub ), mod(β+1, S sub ),…mod(β+S sub -1,S sub ), where β=0,1,…,S sub -1, as shown in Figure 12(d). Figure 12(a) , 12(b) Figures 12(c) and 12(d) demonstrate the alternating order (mod(β1,S)). sub ),mod(β1+1,S sub Fuzzy attributes (T) S An instance of 1ms (where the target is at zero latency, in the range [0,T)) is defined. s Side peaks can be identified using super-resolution algorithms such as Multi-Signal Classification (MUSIC) or Iterative Adaptive Approaches (IAA). Figure 13(a) and 13(b) Elimination. Figure 13(c) shows the results based on the FFT algorithm.

[0101] like Figure 3 As shown, let S sub (Unit: subcarrier number) represents the spacing of RS resource elements (REs) in the frequency domain, S sub ≥2 indicates a comb-like structure, S sym(Unit: symbol number) represents the spacing between RS symbols in the time domain. The current positioning reference signal (PRS) uses S... sym =1,F i (Unit: subcarrier number) represents the interleaving offset in the frequency domain of the i-th RS symbol, T s For OFDM duration, T cp The duration of the cyclic prefix (CP) is T = T cp +T s The duration of the OFDM symbol with added CP. The RS pattern can be obtained via S. sub ,S sym and F i Adjustments will be made.

[0102] Define mod(Z,M)∈{0,1,..M-1} for any integers Z and M, where mod is the modulo operation. The interleaved format is represented with interleaved offsets, such that there is no integer (κ1∈{1,2,…,S) sub -1) makes the following modular equation system true (i.e., the inverse condition):

[0103] mod((F l -F0)κ1,S sub ) = 0, for l = 1, 2, ..., U F -1.

[0104] Among them U F is the number of symbol numbers, l is the symbol index, and F l ∈{0,1,2,…,S sub -1}.

[0105] Typically, the inverse condition can be obtained through U F =2, F1-F0 satisfies, and is consistent with S sub Coprime. One embodiment is U. F =2, F1-F0=1, which eliminates side peaks in the delay domain.

[0106] MUSIC (Multi-Signal Classification):

[0107] MUSIC can be used for, for example Figure 4 The comb-like structure in the frequency domain is shown. U sub and U sym The bandwidth usage and coherence time duration for each snapshot are determined as follows:

[0108]

[0109] U sym =S sym ·U F

[0110] Among them U F It is the number of RS symbols in a snapshot.

[0111] Figure 14 This describes how to select an instance U for each snapshot based on comb-based RS symbols. sub =2S Sub U F =S sub ,S sym =2. "Spatial smoothing" is used to avoid the rank deficiency problem. For (m+1) snapshots, where m = 0, 1, 2, ... (A) m =BS m +N m ,,where N m It's noise, (A) m Let S be a sequence of non-zero RS REs received in m snapshots, without modulation, B be the steering matrix to be estimated (invariant between snapshots), and S be the signal. m It is the magnitude vector. Compared to the m-th snapshot, the (m+1)-th snapshot will be changed in the subcarrier index by S. sub Shift. For the (m+1)th snapshot, the h-th column of the guiding matrix B is...

[0112]

[0113] Note that matrix B cannot distinguish between τ and τ′=τ+k1T s For a non-zero integer k1, regardless of the choice of the interleaving offset, the ambiguity may only occur in τ′=τ+k1T for the proposed interleaving scheme. s This means that from 0 to T s There are no side peaks within the time delay range. This condition that there are no side peaks is satisfied only if the following statement is true: there is no scalar τ′-τ∈(0,T) s This makes the following equation (hereinafter referred to as the "inverse condition") true: For all i = 0, 1, ..., i sub -1,l=0,1,…,U F -1. Note that the equation with the inverse condition above can be equivalently rewritten in the following form: Where κ1′ is any integer.

[0114] Since the MUSIC algorithm is invariant to constant phase rotation, the interleaved sequence F l Equivalent to {F l +β2}, for any Therefore, without loss of generality, assume F0 = 0. Then, for l = 0, the inverse condition is: This leads to Where κ1 is any integer. Based on the assumption τ′-τ∈(0,T) s )κ1∈{1,2,…,S sub -1}, , interleaved sequence {F l} is equivalent to mod(F l +β2,S sub ), and F l ∈{0,1,…,S sub -1} for any l. The inverse condition is the case where l ≠ 0 in general. The equation requires It is an integer, and It is an integer. Therefore, when F0 = 0, this condition is equivalent to the following equation system having no solution κ1: mod(F l κ1,S sub ) = 0, for l = 1, 2, ..., U F -1.

[0115] Typically, it is possible to deal with {F} l Applying a constant phase rotation, the system of equations with inverse conditions becomes mod((F)). l -F0)κ1,S sub ) = 0, for l = 1, 2, ..., U F -1. Typically, the inverse condition can be expressed by U. F =2,F l -F0 is satisfied by the coprime number of S_sub.

[0116] IAA:

[0117] IAA is a super-resolution, mesh algorithm that requires only a single snapshot. Using a fixed number of REs, IAA can achieve better results than MUSIC in terms of delay resolution and Doppler resolution because it does not require "spatial smoothing" and multiple snapshots. Its blurring characteristics with different RS configurations in the delay and Doppler domains show the same results as MUSIC. The perception problem is formulated as V = WS + N, where

[0118]

[0119] It is the vectorization of the unmodulated received non-zero RS RE. Determine the signal bandwidth, and

[0120] The W-th column of h can be written as

[0121]

[0122] , where h represents the h-th grid in the delay and Doppler domain, and h = 0, 1, 2, ..., G, where G represents the grid density, with larger G values ​​indicating denser grids. Matrix W in the IAA exhibits the same structure as matrix B in the MUSIC. Therefore, the conditions for the staggered scheme proposed in the MUSIC section also apply to the IAA.

[0123] Figures 15(a), 15(b), and 15(c) show the alternation order (mod(β1,S)). sub ),mod(β1+1,S sub Another fuzzy characteristic when the target has zero delay (T) S =1ms,S sub =6) Instance. It can be observed again that the range is [0,T] S The side peaks can be eliminated in Figures 15(a) and 15(b) using super-resolution algorithms such as MUSIC or IAA. Figure 15(c) shows the results using IFFT.

[0124] Figures 16(a), 16(b), and 16(c) show the use of the proposed alternation order (mod(β1,S)). sub ),mod(β1+1,S sub The results for the comb-like 4-structure, containing three targets (time delays of 0.1042 ms, 0.2604 ms, and 0.5208 ms, respectively), are shown in Figures 16(a) and 16(b). MUSIC and IAA can successfully distinguish multiple targets, while IFFT (i.e., Figure 16(c)) shows poorer blurring performance. Furthermore, the proposed interleaving scheme can be easily reused by adjusting offsets β1 and β or by finding interleaving patterns that satisfy the above modular equations without a solution.

[0125] It is worth noting that those skilled in the art can appropriately design joint communication and sensing methods and user equipment (UE) according to different system requirements, and these designs are not limited thereto.

[0126] In summary, this invention provides a joint sensing method and related user equipment (UE) for orthogonal frequency domain multiplexing (OFDM) communication systems, which improves the fuzzy function characteristics related to RS modes and algorithms, and utilizes full-cycle interleaved and partial-cycle interleaved comb sensing reference signal modes and super-resolution sensing algorithms.

[0127] Those skilled in the art will readily observe that numerous modifications and alterations can be made to the apparatus and method while retaining the teachings of the invention. Therefore, the above disclosure should be interpreted only within the scope and limits of the appended claims.

Claims

1. A joint sensing method for orthogonal frequency domain multiplexing (OFDM) communication systems, comprising: Multiple reference signal (RS) resource elements (REs) are sent to a sensing terminal from a set of interlaced comb patterns; as well as The plurality of RS resource units are determined to perform full cycle interleaving, partial cycle interleaving, or a combination of full cycle and partial cycle interleaving.

2. The joint sensing method as described in claim 1, wherein the reference signal has an interlaced pattern comprising a sequence of multiple interlaced offsets, each interlaced offset being multiplied by multiple positive integers less than the comb density modulo the comb size, all of which are non-zero.

3. The joint sensing method as described in claim 1, wherein S sub The unit in the subcarrier number represents the spacing between multiple non-zero resource elements (REs) in the frequency domain, S sym The unit in the symbol number represents the spacing between RS symbols in the time domain, F. i The unit representation of subcarrier numbering is i th Interleaving offset in the frequency domain of RS symbols, T s T represents the duration of OFDM. cp The duration of the cyclic prefix (CP) is represented by T = T s +T cp This represents the sum of the OFDM symbol duration and the CP duration.

4. The joint sensing method as described in claim 3, wherein the plurality of ranges are from 0 to T. s The side peaks were eliminated using a super-resolution algorithm.

5. The joint sensing method as described in claim 3, wherein the 2D multi-signal classification (MUSIC) of interleaved comb patterns in the frequency domain employs spatial smoothing to avoid rank deficiency.

6. The joint sensing method as described in claim 5, wherein the maximum unambiguous 2D range around the main peak is a time delay from 0 to Ts, and from 1 to... The Doppler frequency, where I is a specified value and 7. The joint sensing method as described in claim 5, wherein multiple snapshots are used for MUSIC.

8. The joint sensing method of claim 7, wherein the bandwidth occupied is determined based on the repetition time of an interlaced pattern in one of a plurality of snapshots and the number of reference symbols in the interlaced pattern.

9. The joint sensing method as described in claim 3, wherein a single snapshot of an interlaced pattern is used for IAA super-resolution, a grid algorithm with a fixed number of REs, and no spatial smoothing.

10. The joint sensing method of claim 9, wherein the maximum unambiguous 2D range around the main peak is a time delay from 0 to Ts, and from 1 to... The Doppler frequency, where I is a specified value and 11. A user equipment (UE) for an orthogonal frequency domain multiplexing (OFDM) communication system, comprising: A wireless transceiver configured to perform wireless transmission and reception with a service terminal; as well as A controller configured to determine multiple RS resource units to perform full cycle interleaving, partial cycle interleaving, or a combination of full cycle and partial cycle interleaving.

12. The UE of the OFDM communication system as claimed in claim 11, wherein the reference signal has an interleaved pattern comprising a sequence of multiple interleaved offsets, each interleaved offset being multiplied by a plurality of non-zero positive integers less than the comb density modulo the comb size.

13. The UE of the OFDM communication system as described in claim 11, wherein S sub The unit in the subcarrier number represents the spacing between multiple non-zero resource elements (REs) in the frequency domain, S sym The unit in the symbol number represents the spacing between RS symbols in the time domain, F. i The unit representation of subcarrier numbering is i th Interleaving offset in the frequency domain of RS symbols, T s T represents the duration of OFDM. cp The duration of the cyclic prefix (CP) is represented by T = T s +T cp This represents the sum of the OFDM symbol duration and the CP duration.

14. The UE of the OFDM communication system as described in claim 13, wherein the plurality of ranges are 0 to T. s The side peaks were eliminated using a super-resolution algorithm.

15. The UE of the OFDM communication system as claimed in claim 13, wherein the 2D multiple signal classification (MUSIC) of the interlaced comb pattern in the frequency domain employs spatial smoothing to avoid rank deficiency.

16. The UE of the OFDM communication system as described in claim 15, wherein the maximum unambiguous 2D range around the main peak is the time delay from 0 to Ts, and I to The Doppler frequency, where I is a specified value and 17. The UE of the OFDM communication system as claimed in claim 15, wherein multiple snapshots are used for MUSIC.

18. The UE of the OFDM communication system of claim 17, wherein the occupied bandwidth is determined based on the repetition time of an interlaced pattern in one of a plurality of snapshots and the number of reference symbols in the interlaced pattern.

19. The UE of the OFDM communication system as claimed in claim 13, wherein a single snapshot of the interlaced pattern is used for an IAA super-resolution, fixed-number RE grid algorithm without spatial smoothing.

20. The UE of the OFDM communication system as described in claim 19, wherein the maximum unambiguous 2D range around the main peak is the time delay from 0 to Ts, and I to The Doppler frequency, where I is a specified value and

Images