A scanning start beam points to zero VICTS array antenna

Abstract

The application discloses a VICTS array antenna with a scanning starting beam pointing to zero, which comprises a feeding network and a radiation network. 10 The feeding network comprises a power division network, a slow wave structure, a parallel plate waveguide and a line source generator. 10 The power division network divides TE 10 waves into n TE waves and outputs the n TE waves to the line source generator. The line source generator synthesizes and converts the n TE waves into quasi-TEM waves and outputs the quasi-TEM waves to the parallel plate waveguide. The parallel plate waveguide transmits the quasi-TEM waves to the radiation network. The radiation network radiates the quasi-TEM waves to free space. The slow wave structure and the parallel plate waveguide are coupled to change the equivalent guided wave wavelength of the parallel plate waveguide. The slow wave structure comprises a rotating disc and a plurality of pins. The rotating disc is provided with a downwardly recessed curved surface on the top. The plurality of pins are arranged on the curved surface to form a pin array. The row spacing of the pin array is greater than the column spacing. The VICTS array antenna can realize scanning starting beam pointing to zero in the whole frequency band of 14-14.5 GHz satellite communication frequency band, has no scanning blind area and can meet the demand of large scanning range in current satellite communication.

Description

TECHNICAL FIELD

[0001] The present application relates to a VICTS array antenna, in particular to a VICTS array antenna with a scan starting beam pointing to zero. BACKGROUND

[0002] With the development of satellite communication technology, mobile satellite terminals and other devices have higher requirements for the profile, cost and beam scanning range of the antenna. VICTS (Variable Inclination Continuous Transverse Stub) array antenna has become a core candidate antenna due to its simple structure, low profile and large scanning angle.

[0003] The conventional VICTS array antenna usually includes a radiation network and a feed network. The feed network is used to feed the radio frequency signal output by the front-end device into the radiation network. The radiation network radiates the radio frequency signal output by the feed network to the free space. The radiation network includes a plurality of CTS radiation stubs, and the plurality of CTS radiation stubs are uniformly and spacedly distributed. The existing feed network usually includes a power division network, a slow wave structure, a parallel plate waveguide (PPW) and a linear source generator (LSG). The power division network is connected with the linear source generator, the linear source generator is connected with the parallel plate waveguide, and the slow wave structure is realized by opening a plurality of grooves periodically distributed on the lower surface of the parallel plate waveguide.

[0004] The conventional VICTS array antenna realizes beam scanning by the relative rotation of the radiation network and the feed network. However, the VICTS array antenna can only realize the matching of the equivalent waveguide wavelength of the parallel plate waveguide and the interval of the CTS radiation stub at one frequency point. The equivalent waveguide wavelength of the parallel plate waveguide and the interval of the CTS radiation stub are not equal at other frequency points. Thus, in the satellite communication frequency band of 14-14.5 GHz, only the beam at one frequency point can start scanning from the normal 0°. The starting beams at other working frequencies cannot point to the normal 0°. The angle range that cannot be covered due to the offset of the starting beam forms a large scanning blind area, which reduces the coverage range of the VICTS array antenna and makes it difficult to meet the current demand for large scanning range in satellite communication.

[0005] A wideband and large coverage continuous beam steering antenna based on variable inclination continuous transverse stub (VICTS) technology is proposed in the paper “Wideband and Large Coverage Continuous Beam Steering Antenna Based on Variable Inclination Continuous Transverse Stub Technology”. The slow wave structure of the VICTS beam scanning antenna is also a traditional structure with grooves opened on the lower surface of the parallel plate waveguide. The test results show that the beam of the VICTS beam scanning antenna can be scanned from the normal 0° at the center frequency point 15 GHz in the 12-18 GHz operating frequency band. When deviating from the center frequency point ±2 GHz, the starting pointing of the beam has deviated to the normal ±7°. Thus, the VICTS beam scanning antenna has obvious scanning blind area at the edge of its operating frequency band (the angle range that cannot be covered due to the deviation of the starting beam), and it is difficult to meet the current demand for large scanning range in satellite communication. SUMMARY

[0006] The technical problem to be solved by the present application is to provide a VICTS array antenna with zero starting beam pointing, which can scan the starting beam pointing at zero at all frequency points in the 14-14.5 GHz satellite communication frequency band, has no scanning blind area, and can meet the current demand for large scanning range in satellite communication.

[0007] The technical solution adopted by the present application to solve the above technical problem is as follows: a VICTS array antenna with zero starting beam pointing, comprising a feed network and a radiation network; the radiation network comprises a plurality of CTS radiation branches which are uniformly and spacedly distributed; the feed network comprises a power division network, a slow wave structure, a parallel plate waveguide and a line source generator; the power division network is used for equally dividing the TE 10 wave input from outside into n paths of TE 10 wave output to the line source generator, n is an integer greater than or equal to 4; the line source generator is used for converting the n paths of TE 10The wave is synthesized and converted into quasi-TEM wave and output to the parallel plate waveguide; the slow wave structure is used to couple with the parallel plate waveguide to change the equivalent guided wave wavelength of the parallel plate waveguide; the parallel plate waveguide is used to transmit the quasi-TEM wave to a plurality of CTS radiation branches; the plurality of CTS radiation branches are used to radiate the quasi-TEM wave to free space; the slow wave structure is arranged below the parallel plate waveguide and has a gap between the two, the gap is not greater than 1mm, the slow wave structure comprises a cylindrical rotating disc and a plurality of pins, the rotating disc can be rotated under force; the top of the rotating disc is provided with a downwardly recessed curved surface; the plurality of pins are arranged on the curved surface and arranged in a plurality of rows and columns to form a pin array, and the arrangement of the pin array on the curved surface is anisotropic.

[0008] Compared with the prior art, the advantages of the present application are that the slow wave structure is arranged below the parallel plate waveguide, the rotating disc under force and the pin array constitute the slow wave structure, when the slow wave structure rotates, the relative position of the pin array and the parallel plate waveguide changes; because the arrangement of the pin array on the curved surface is anisotropic, that is, the pin array has different periodicity in different directions in the arrangement plane, when the rotating disc rotates, the equivalent pin spacing in the transmission direction of the quasi-TEM wave in the parallel plate waveguide changes; thus, when the relative position of the pin array and the parallel plate waveguide changes, the pin spacing in the transmission direction of the quasi-TEM wave in the parallel plate waveguide changes, at this time, different electromagnetic medium effects are introduced into the parallel plate waveguide, and the electromagnetic confinement effect of the slow wave structure on the quasi-TEM wave transmitted in the parallel plate waveguide also changes; the strength of the electromagnetic confinement effect of the slow wave structure on the quasi-TEM wave transmitted in the parallel plate waveguide directly affects the equivalent dielectric constant of the parallel plate waveguide, when the electromagnetic confinement effect of the slow wave structure on the quasi-TEM wave transmitted in the parallel plate waveguide changes, the equivalent guided wave wavelength of the parallel plate waveguide also changes; thus, the present application can change the relative position of the pin array and the parallel plate waveguide by rotating the rotating disc at each frequency point in the 14-14.5GHz frequency band, different electromagnetic medium effects are introduced into the parallel plate waveguide, the equivalent guided wave wavelength of the parallel plate waveguide is equal to the distance between two adjacent CTS radiation branches, so that the scanning starting beam at each frequency point in the 14-14.5GHz frequency band can be directed to zero, there is no scanning blind area, and the large scanning range requirement in current satellite communication can be met; the experimental simulation results show that the overall reflection coefficient |S 11 | of the present application is less than -10dB in the 14-14.5GHz working frequency band, the maximum scanning angle is ±60°, the gain drop is less than 5dB when the scanning angle is 60°, large angle scanning can be realized, and the scanning starting beam at each frequency point is zero.

[0009] Further, the row spacing of the pin array is greater than the column spacing.

[0010] Further, the power division network has one input end and n output ends; the n output ends of the power division network are distributed in a curve, and the curvature of the curve is equal to the curvature of the curved surface; the line source generator has n input ends and one output end; the n input ends of the line source generator are distributed in a curve, and the curvature of the curve is equal to the curvature of the curved surface; the parallel plate waveguide has a cuboid structure, and has one input end and one output end; the input end of the power division network is used for accessing the externally input TE 10 waves, the n output ends of the power division network are connected to the n input ends of the line source generator one by one, and are used for outputting n paths of TE 10 waves to the n input ends of the line source generator one by one; the output end of the line source generator is connected to the input end of the parallel plate waveguide, and is used for outputting the quasi-TEM wave to the parallel plate waveguide; and the output end of the parallel plate waveguide is used for transmitting the quasi-TEM wave to the plurality of CTS radiation branches.

[0011] Further, n = 12, the power division network comprises 7 power dividers, 4 3dB couplers, 8 delay line phase shifters and 8 tapered single-ridge waveguide phase shifters; the 7 power dividers are respectively a first power divider, a second power divider, a third power divider, a fourth power divider, a fifth power divider, a sixth power divider and a seventh power divider; the first power divider is a mirror-symmetrical equal division power divider; the second power divider, the third power divider, the fourth power divider, the fifth power divider, the sixth power divider and the seventh power divider are all unequal division power dividers, which are used for dividing the electromagnetic wave signals input thereinto into two routes of electromagnetic waves with same amplitude and unequal phase; the 4 3dB couplers are respectively a first 3dB coupler, a second 3dB coupler, a third 3dB coupler and a fourth 3dB coupler; the 8 delay line phase shifters are respectively a first line phase shifter, a second line phase shifter, a third line phase shifter, a fourth line phase shifter, a fifth line phase shifter, a sixth line phase shifter, a seventh line phase shifter and an eighth line phase shifter; the 8 tapered single-ridge waveguide phase shifters are respectively a first waveguide phase shifter, a second waveguide phase shifter, a third waveguide phase shifter, a fourth waveguide phase shifter, a fifth waveguide phase shifter, a sixth waveguide phase shifter, a seventh waveguide phase shifter and an eighth waveguide phase shifter; the first 3dB coupler, the second 3dB coupler, the first line phase shifter, the second line phase shifter, the third line phase shifter, the fourth line phase shifter, the second power divider, the third power divider, the fourth power divider, the first waveguide phase shifter, the second waveguide phase shifter, the third waveguide phase shifter and the fourth waveguide phase shifter constitute a first power division path; the third 3dB coupler, the fourth 3dB coupler, the fifth line phase shifter, the sixth line phase shifter, the seventh line phase shifter, the eighth line phase shifter, the fifth power divider, the sixth power divider, the seventh power divider, the fifth waveguide phase shifter, the sixth waveguide phase shifter, the seventh waveguide phase shifter and the eighth waveguide phase shifter constitute a second power division path; a plane that makes the first power divider mirror-symmetrical is called a symmetry plane, the second power division path is mirror-symmetrical to the first power division path about the symmetry plane; the first power divider serves as an input stage, which equally divides the TE 10 wave input thereinto into two routes of TE 10 waves with same amplitude and equal phase, and outputs the two routes of TE 10 waves to the first power division path and the second power division path respectively, the first power division path and the second power division path divide the TE 10 waves thereinto into six routes of TE

[0012] Further, each power divider has an input end, a first output end and a second output end; each 3dB coupler has an input end, a first output end and a second output end; each delay line phase shifter has one input end and one output end; each tapered single-ridge waveguide phase shifter has one input end and one output end; the first output end of the first power divider is connected with the input end of the first 3dB coupler, the first output end of the first 3dB coupler is connected with the input end of the first line phase shifter, the output end of the first line phase shifter is connected with the input end of the second 3dB coupler, the first output end of the second 3dB coupler is connected with the input end of the second line phase shifter, the output end of the second line phase shifter is connected with the input end of the first waveguide phase shifter, the second output end of the second 3dB coupler is connected with the input end of the second power divider, the first output end of the second power divider is connected with the input end of the third line phase shifter, the output end of the third line phase shifter is connected with the input end of the second waveguide phase shifter, the second output end of the first 3dB coupler is connected with the input end of the third power divider, the first output end of the third power divider is connected with the input end of the fourth line phase shifter, the output end of the fourth line phase shifter is connected with the input end of the third waveguide phase shifter, the second output end of the third power divider is connected with the input end of the fourth power divider, the first output end of the fourth power divider is connected with the input end of the fourth waveguide phase shifter; the third 3dB coupler is mirror-symmetrical to the first 3dB coupler about the symmetry plane; the fourth 3dB coupler and the second 3dB coupler are mirror-symmetrical about the symmetry plane; the fifth power divider is mirror-symmetrical to the second power divider about the symmetry plane; the sixth power divider is mirror-symmetrical to the third power divider about the symmetry plane; the seventh power divider is mirror-symmetrical to the fourth power divider about the symmetry plane; the fifth line phase shifter is mirror-symmetrical to the first line phase shifter about the symmetry plane; the sixth line phase shifter and the second line phase shifter are mirror-symmetrical about the symmetry plane; the seventh line phase shifter and the third line phase shifter are mirror-symmetrical about the symmetry plane; the eighth line phase shifter and the fourth line phase shifter are mirror-symmetrical about the symmetry plane; the fifth waveguide phase shifter is mirror-symmetrical to the first waveguide phase shifter about the symmetry plane; the sixth waveguide phase shifter is mirror-symmetrical to the second waveguide phase shifter about the symmetry plane; the seventh waveguide phase shifter is mirror-symmetrical to the third waveguide phase shifter about the symmetry plane; the eighth waveguide phase shifter is mirror-symmetrical to the fourth waveguide phase shifter about the symmetry plane; the input end of the first power divider is the input end of the power division network; the output end of the first waveguide phase shifter, the output end of the second waveguide phase shifter, the second output end of the second power divider, the output end of the third waveguide phase shifter, the output end of the fourth waveguide phase shifter, the second output end of the fourth power divider, the second output end of the seventh power divider, the output end of the eighth waveguide phase shifter, the output end of the seventh waveguide phase shifter, the second output end of the fifth power divider, the output end of the sixth waveguide phase shifter and the output end of the fifth waveguide phase shifter are the 12 output ends of the power division network. BRIEF DESCRIPTION OF DRAWINGS

[0013] Figure 1 This is a schematic diagram of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention;

[0014] Figure 2 This is a front view of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention;

[0015] Figure 3 This is a top view of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention;

[0016] Figure 4 An exploded view of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention;

[0017] Figure 5 This is a schematic diagram of the radiation network of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention.

[0018] Figure 6 This is a top view of the radiation network of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention.

[0019] Figure 7 This is a front view of the radiation network of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention.

[0020] Figure 8 This is a schematic diagram of the slow-wave structure of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention.

[0021] Figure 9 for Figure 8 Enlarged view of section A;

[0022] Figure 10 This is a top view of the slow-wave structure of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention.

[0023] Figure 11 for Figure 10 Enlarged view of section B;

[0024] Figure 12 This is a front view of the slow-wave structure of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention.

[0025] Figure 13 This is a schematic diagram of the power divider network of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention.

[0026] Figure 14 This is a top view of the power divider network of the VICTS array antenna with the scanning start beam pointing to zero according to the present invention;

[0027] Figure 15 The simulation diagram of the reflection coefficient corresponding to the radiation network relative to the feed network respectively rotating 0°, 20° and 40° when the slow wave structure of the scanning starting beam pointing to the zero VICTS array antenna of the application is relative to the parallel plate waveguide rotating 0° in the full frequency band of 14-14.5 GHz;

[0028] Figure 16 The simulation diagram of the reflection coefficient corresponding to the radiation network relative to the feed network respectively rotating 0°, 20° and 40° when the slow wave structure of the scanning starting beam pointing to the zero VICTS array antenna of the application is relative to the parallel plate waveguide rotating 45° in the full frequency band of 14-14.5 GHz;

[0029] Figure 17 The simulation diagram of the reflection coefficient corresponding to the radiation network relative to the feed network respectively rotating 0°, 20° and 40° when the slow wave structure of the scanning starting beam pointing to the zero VICTS array antenna of the application is relative to the parallel plate waveguide rotating 90° in the full frequency band of 14-14.5 GHz;

[0030] Figure 18 The normalized radiation pattern when the radiation network relative to the feed network respectively rotates 0°, 20° and 40° when the slow wave structure of the scanning starting beam pointing to the zero VICTS array antenna of the application is relative to the parallel plate waveguide rotating 0° and the working frequency is 14 GHz;

[0031] Figure 19 The normalized radiation pattern when the radiation network relative to the feed network respectively rotates 0°, 20° and 40° when the slow wave structure of the scanning starting beam pointing to the zero VICTS array antenna of the application is relative to the parallel plate waveguide rotating 45° and the working frequency is 14.2 GHz;

[0032] Figure 20 The normalized radiation pattern when the radiation network relative to the feed network respectively rotates 0°, 20° and 40° when the slow wave structure of the scanning starting beam pointing to the zero VICTS array antenna of the application is relative to the parallel plate waveguide rotating 90° and the working frequency is 14.5 GHz. DETAILED DESCRIPTION

[0033] The application will be further described in detail below with reference to the drawings.

[0034] Example one: as Figures 1 to 12 ( Figures 1 to 12All the structures shown are air model structures, and the cavities correspond to metal entities, while the entity parts correspond to cavities. As shown, a VICTS array antenna with a scanning starting beam pointing to zero includes a feed network and a radiation network 1; the radiation network 1 includes a plurality of CTS radiation branches 2, which are uniformly spaced; the feed network includes a power division network 3, a slow wave structure 4, a parallel plate waveguide 5, and a line source generator 6; the power division network 3 is used to divide the externally input TE 10 waves into n paths of TE 10 wave outputs to the line source generator 6, n is an integer greater than or equal to 4; the line source generator 6 is used to synthesize and convert the n paths of TE 10 waves into quasi-TEM waves and output them to the parallel plate waveguide 5; the slow wave structure 4 is used to couple with the parallel plate waveguide 5 to change the equivalent guided wave wavelength of the parallel plate waveguide 5; the parallel plate waveguide 5 is used to transmit the quasi-TEM waves to the plurality of CTS radiation branches 2; the plurality of CTS radiation branches 2 are used to radiate the quasi-TEM waves to the free space; the slow wave structure 4 is arranged below the parallel plate waveguide 5, and there is a gap between the two, which is not greater than 1 mm; the slow wave structure 4 includes a cylindrical rotating disc 7 and a plurality of pins 8; the rotating disc 7 can rotate under force, and the top of the rotating disc 7 is provided with a downwardly recessed curved surface 9; the plurality of pins 8 are arranged on the curved surface 9 in the form of a pin array in multiple rows and multiple columns; the arrangement of the pin array on the curved surface is anisotropic.

[0035] In this embodiment, the row spacing L1 of the pin array is greater than the column spacing L2.

[0036] In the embodiment, the slow wave structure 4 is arranged below the parallel plate waveguide 5 by spacing, and the slow wave structure 4 is composed of a rotating disc 7 and a pin array which can be rotated by force, and the pin array is anisotropic on the curved surface, because the row spacing L1 and the column spacing L2 of the pin array are not equal, that is, the pin array has different periodicity in different directions on the arrangement surface, so that when the rotating disc 7 rotates, the equivalent pin spacing in the transmission direction of the quasi-TEM wave in the parallel plate waveguide 5 changes; thus, when the slow wave structure 4 rotates, the relative position of the pin array of the slow wave structure 4 and the parallel plate waveguide 5 changes, and the pin spacing 8 in the transmission direction of the quasi-TEM wave in the parallel plate waveguide 5 also changes, at this time, different electromagnetic medium effects are introduced into the parallel plate waveguide 5, and the electromagnetic confinement effect of the slow wave structure 4 on the quasi-TEM wave transmitted in the parallel plate waveguide 5 also changes; the strength of the electromagnetic confinement effect of the slow wave structure 4 on the quasi-TEM wave transmitted in the parallel plate waveguide 5 directly affects the equivalent dielectric constant of the parallel plate waveguide 5, and when the electromagnetic confinement effect of the slow wave structure 4 on the quasi-TEM wave transmitted in the parallel plate waveguide 5 changes, the equivalent waveguide wavelength of the parallel plate waveguide 5 also changes; thus, the present application can change the relative position of the pin array and the parallel plate waveguide 5 by rotating the rotating disc 7 at each frequency point in the 14-14.5 GHz frequency band, introduce different electromagnetic medium effects for the parallel plate waveguide 5, make the equivalent waveguide wavelength of the parallel plate waveguide 5 equal to the spacing between two adjacent CTS radiating branches 2, so that the starting beams of the full-frequency-point scanning in the 14-14.5 GHz frequency band can all point to zero, there is no scanning blind area, and the demand for a large scanning range in current satellite communication can be met.

[0037] Embodiment two: the embodiment is basically the same as embodiment one, and the difference lies in that: in the embodiment, the power division network 3 has one input end and n output ends; the n output ends of the power division network 3 are distributed in a curve, and the curve curvature is equal to the curvature of the curved surface 9; the line source generator 6 has n input ends and one output end; the n input ends of the line source generator 6 are distributed in a curve, and the curve curvature is equal to the curvature of the curved surface 9; the parallel plate waveguide 5 has a cuboid structure and has one input end and one output end; the input end of the power division network 3 is used for accessing the externally input TE 10 wave, the n output ends of the power division network 3 are connected with the n input ends of the line source generator 6 in one-to-one correspondence, and are used for outputting n TE 10 waves to the n input ends of the line source generator 6 in one-to-one correspondence; the output end of the line source generator 6 is connected with the input end of the parallel plate waveguide 5, and is used for outputting the quasi-TEM wave to the parallel plate waveguide 5; and the output end of the parallel plate waveguide 5 is used for transmitting the quasi-TEM wave to the plurality of CTS radiating branches 2.

[0038] In the embodiment, since the slow wave structure 4 is a disc structure, compared with electromagnetic waves far from the center of the disc, electromagnetic waves at the middle position will enter the slow wave structure 4 in advance when the electromagnetic waves are transmitted on the slow wave structure 4, so that the equal phase surface is not a straight line, but an arc line with the phase in advance at both ends and the phase lag in the middle, so that the feeding phases are inconsistent. The inconsistent feeding phases will cause the deterioration of the directional diagram of the VICTS array antenna. Therefore, by making the n input ends of the line source generator 6 and the n output ends of the power dividing network 3 be in curve distribution, and the curvature of the curve is equal to the curvature of the curved surface 9, and by the cooperation of the above curve distribution design, the conformal design of the slow wave structure 4, the line source generator 6 and the power dividing network 3 is realized, the inconsistent feeding phases generated at the slow wave structure 4 are compensated by the cooperation of the power dividing network 3 and the line source generator 6, so that the feeding phases of the electromagnetic waves fed into the radiating network 1 are consistent, thereby avoiding the deterioration of the directional diagram of the VICTS array antenna.

[0039] Embodiment three: the embodiment is basically the same as embodiment two, the difference is that in the embodiment, as shown in FIG. 3, the curved surface 9 is a circular arc surface, and the n input ends of the line source generator 6 and the n output ends of the power dividing network 3 are arranged in curve distribution on the curved surface 9. Figure 13 and Figure 14As shown, n = 12, the power division network 3 includes 7 power dividers, 4 3dB couplers, 8 delay line phase shifters and 8 tapered single-ridge waveguide phase shifters; the 7 power dividers are respectively a first power divider 10, a second power divider 11, a third power divider 12, a fourth power divider 13, a fifth power divider 14, a sixth power divider 15 and a seventh power divider 16; the first power divider 10 is a mirror-symmetrical equal-division power divider; the second power divider 11, the third power divider 12, the fourth power divider 13, the fifth power divider 14, the sixth power divider 15 and the seventh power divider 16 are all unequal-division power dividers, which are used to divide the electromagnetic wave signals input thereto into two routes of electromagnetic waves with same amplitude and unequal phase; the 4 3dB couplers are respectively a first 3dB coupler 17, a second 3dB coupler 18, a third 3dB coupler 19 and a fourth 3dB coupler 20; the 8 delay line phase shifters are respectively a first line phase shifter 21, a second line phase shifter 22, a third line phase shifter 23, a fourth line phase shifter 24, a fifth line phase shifter 25, a sixth line phase shifter 26, a seventh line phase shifter 27 and an eighth line phase shifter 28; the 8 tapered single-ridge waveguide phase shifters are respectively a first waveguide phase shifter 29, a second waveguide phase shifter 30, a third waveguide phase shifter 31, a fourth waveguide phase shifter 32, a fifth waveguide phase shifter 33, a sixth waveguide phase shifter 34, a seventh waveguide phase shifter 35 and an eighth waveguide phase shifter 36; the first 3dB coupler 17, the second 3dB coupler 18, the first line phase shifter 21, the second line phase shifter 22, the third line phase shifter 23, the fourth line phase shifter 24, the second power divider 11, the third power divider 12, the fourth power divider 13, the first waveguide phase shifter 29, the second waveguide phase shifter 30, the third waveguide phase shifter 31 and the fourth waveguide phase shifter 32 constitute a first power division path; the third 3dB coupler 19, the fourth 3dB coupler 20, the fifth line phase shifter 25, the sixth line phase shifter 26, the seventh line phase shifter 27, the eighth line phase shifter 28, the fifth power divider 14, the sixth power divider 15, the seventh power divider 16, the fifth waveguide phase shifter 33, the sixth waveguide phase shifter 34, the seventh waveguide phase shifter 35 and the eighth waveguide phase shifter 36 constitute a second power division path; a plane that makes the first power divider 10 mirror-symmetrical is referred to as a symmetry plane S1, the second power division path and the first power division path are mirror-symmetrical about the symmetry plane S1; the first power divider 10 serves as an input stage, divides the TE 10 wave input thereto into two routes of TE 10 waves with same amplitude and equal phase, and outputs the two routes of TE 10 waves to the first power division path and the second power division path respectively, the first power division path and the second power division path divide the TE 10 waves input thereto into 6 routes of TE waves that are mirror-symmetrical, and output the 6 routes of TE

[0040] In the embodiment, each power divider has an input end, a first output end and a second output end; each 3dB coupler has an input end, a first output end and a second output end; each delay line phase shifter has one input end and one output end; each tapered single-ridge waveguide phase shifter has one input end and one output end; the first output end of the first power divider 10 is connected with the input end of the first 3dB coupler 17, the first output end of the first 3dB coupler 17 is connected with the input end of the first line phase shifter 21, the output end of the first line phase shifter 21 is connected with the input end of the second 3dB coupler, the first output end of the second 3dB coupler is connected with the input end of the second line phase shifter 22, the output end of the second line phase shifter 22 is connected with the input end of the first waveguide phase shifter 29, the second output end of the second 3dB coupler is connected with the input end of the second power divider 11, the first output end of the second power divider 11 is connected with the input end of the third line phase shifter 23, the output end of the third line phase shifter 23 is connected with the input end of the second waveguide phase shifter 30, the second output end of the first 3dB coupler 17 is connected with the input end of the third power divider 12, the first output end of the third power divider 12 is connected with the input end of the fourth line phase shifter 24, the output end of the fourth line phase shifter 24 is connected with the input end of the third waveguide phase shifter 31, the second output end of the third power divider 12 is connected with the input end of the fourth power divider 13, the first output end of the fourth power divider 13 is connected with the input end of the fourth waveguide phase shifter 32; the third 3dB coupler is mirror-symmetrical about the symmetry plane S1 with the first 3dB coupler 17; the fourth 3dB coupler 20 is mirror-symmetrical about the symmetry plane S1 with the second 3dB coupler 18; the fifth power divider 14 is mirror-symmetrical about the symmetry plane S1 with the second power divider 11; the sixth power divider 15 is mirror-symmetrical about the symmetry plane S1 with the third power divider 12; the seventh power divider 16 is mirror-symmetrical about the symmetry plane S1 with the fourth power divider 13; the fifth line phase shifter 25 is mirror-symmetrical about the symmetry plane S1 with the first line phase shifter 21; the sixth line phase shifter 26 is mirror-symmetrical about the symmetry plane S1 with the second line phase shifter 22; the seventh line phase shifter 27 is mirror-symmetrical about the symmetry plane S1 with the third line phase shifter 23; the eighth line phase shifter 28 is mirror-symmetrical about the symmetry plane S1 with the fourth line phase shifter 24; the fifth waveguide phase shifter 33 is mirror-symmetrical about the symmetry plane S1 with the first waveguide phase shifter 29; the sixth waveguide phase shifter 34 is mirror-symmetrical about the symmetry plane S1 with the second waveguide phase shifter 30; the seventh waveguide phase shifter 35 is mirror-symmetrical about the symmetry plane S1 with the third waveguide phase shifter 31; the eighth waveguide phase shifter 36 is mirror-symmetrical about the symmetry plane S1 with the fourth waveguide phase shifter 32; the input end of the first power divider 10 is the input end of the power division network 3;The output terminals of the first waveguide phase shifter 29, the second waveguide phase shifter 30, the second power divider 11, the third waveguide phase shifter 31, the fourth waveguide phase shifter 32, the fourth power divider 13, the seventh power divider 16, the eighth waveguide phase shifter 36, the seventh waveguide phase shifter 35, the fifth power divider 14, the sixth waveguide phase shifter 34, and the fifth waveguide phase shifter 33 serve as the 12 output terminals P1 to P12 of the power dividing network 3.

[0041] In this embodiment, when an external TE... 10 When the wave is input to the input terminal of the first power divider 10, the first power divider 10 will convert the TE signal into a signal. 10 The wave is divided into two TE channels with equal amplitude and phase. 10 The wave is output to the first power splitting path and the second power splitting path respectively through its first output terminal and second output terminal. In the first power splitting path, TE 10 Wave input to first 3dB coupler 17, first 3dB coupler 17 to TE 10 The wave is directionally coupled and split to obtain two TE channels. 10 Wave, one of the TE paths 10 The wave output is sent to the first line phase shifter 21, and the other TE is sent to the second line. 10 The wave output is sent to the third power divider 12; the first line phase shifter 21 adjusts the TE input at its input terminal. 10 The transmission path length of the wave, for this path TE 10 Phase compensation is performed on the wave to initially eliminate the TE signal in this path. 10 After the phase deviation caused by the difference in the propagation path with other branches, the output is sent to the second 3dB coupler 18. The second 3dB coupler 18 is connected to the TE at its input terminal. 10 The wave is directionally coupled and split to obtain two TE channels. 10 Wave, one of the TE paths 10 The wave output is sent to the second-line phase shifter 22, and another TE is sent to the second-line phase shifter 22. 10 The wave output is sent to the second power divider 11. The second line phase shifter 22 connects to the TE at its input terminal. 10 After phase adjustment, the wave is output to the first waveguide phase shifter 29; the first waveguide phase shifter 29, based on the ridge waveguide gradient characteristics, adjusts the phase of the connected TE waveguide. 10 The wave undergoes phase fine-tuning, while optimizing TE. 10 Impedance matching of wave propagation reduces TE 10 The wave reflection loss is ultimately output at the first output terminal P1 of the power divider network 3; the second power divider 11, according to the output requirements of the power divider network 3, outputs to the connected TE... 10 Differentiated allocation of the wave, and the TE 10 Two TE channels with the same amplitude.10 One output path goes to the third-line phase shifter 23, and the other outputs at the third output terminal P3 of the power divider network 3; the third-line phase shifter 23 outputs to the connected TE 10 Phase compensation is performed on the wave to correct the TE path. 10 The phase deviation generated during transmission in the second power divider 11 is then output to the second waveguide phase shifter 30; the second waveguide phase shifter 30 outputs to the connected TE 10 The wave undergoes phase fine-tuning and impedance matching optimization, outputting at the second output terminal P2 of power divider network 3; the third power divider 12 connects it to TE. 10 Two TE channels with the same amplitude. 10 Wave, one of the TE paths 10 The wave output is sent to the fourth line phase shifter 24, and another TE is sent to the fourth line phase shifter 2 10 The wave output is sent to the fourth power divider 13; the third power divider 12 and the second power divider 11 use the same power dividing principle to achieve TE. 10 Further multi-stage distribution of the wave; the fourth-line phase shifter 24 to its connected TE 10 Phase compensation is performed on the wave to correct TE. 10 The phase deviation of the wave during transmission in the third power divider 12 is then output to the third waveguide phase shifter 31; the third waveguide phase shifter 31 outputs its connected TE... 10 The wave undergoes phase fine-tuning and impedance matching optimization, outputting at the fourth output terminal P4 of power divider network 3; the fourth power divider 13 connects it to the TE. 10 Two TE channels with the same amplitude. 10 Wave, further expanding the output branches, one TE 10 The wave output is sent to the fourth waveguide phase shifter 32, and another TE... 10 The wave is output at the sixth output terminal P6 of the power divider network 3; the fourth waveguide phase shifter 32 outputs to the connected TE. 10 The wave undergoes phase fine-tuning and is output at the fifth output terminal P5 of power divider network 3; thus, the first power divider path achieves TE. 10 The wave is distributed at the first output terminal P1 to the sixth output terminal P6 of power divider network 3. The second power divider path similarly implements TE. 10 The distribution of the wave at the 7th output terminal P7 to the 12th output terminal P12 of the power divider network 3. Since the second power divider path is a mirror image of the first power divider path, the TE outputs from the 12 output terminals of the power divider network 3... 10 The wave can meet the preset phase requirements, thereby achieving phase compensation and meeting the needs of the subsequent line source generator 6 to synthesize quasi-TEM waves.

[0042] In this embodiment, the first power divider 10 serves as the input stage, ensuring that the TE connections of the first and second power divider paths are connected. 10The absence of phase difference in the wave provides a balanced initial signal foundation for subsequent multi-stage signal distribution in the first and second power distribution paths, avoiding deviations in subsequent power distribution due to uneven amplitude and phase of the initial signal. The 3dB coupler accurately splits the TE signal. 10 While simulating wave propagation, it effectively isolates the TE signals of different output branches. 10 Wave, reduce TE between branches 10 Crosstalk, maintaining branch TE 10 The low crosstalk characteristics of the wave ensure the TE of each split path. 10 Wave independence. The second power divider 11, third power divider 12, fourth power divider 13, fifth power divider 14, sixth power divider 15, and seventh power divider 16 implement power distribution at the 12 outputs of the power dividing network 3 as needed. Delay line phase shifters and tapered single-ridge waveguide phase shifters are used for TE... 10 Phase deviation during wave transmission is compensated. Power divider network 3 effectively compensates for the inconsistency in the feed phase generated at slow wave structure 4. Line source generator 6, power divider network 3 and slow wave structure adopt a conformal design to ensure that the electromagnetic wave feed phase of the radiation network 1 fed into the parallel plate waveguide 5 remains consistent.

[0043] To verify the performance of the VICTS array antenna of this invention, simulations were performed at various scanning angles. Specifically, within the 14-14.5 GHz full frequency band, when the slow-wave structure rotates 0° relative to the parallel plate waveguide, the reflection coefficients corresponding to rotations of the radiating network relative to the feed network of 0°, 20°, and 40° are as follows: Figure 15 As shown. Within the 14-14.5 GHz full frequency band, when the slow wave structure is rotated 45° relative to the parallel plate waveguide, the reflection coefficients corresponding to rotations of the radiating network relative to the feeding network of 0°, 20°, and 40° are as follows: Figure 16 As shown. Within the 14-14.5 GHz full frequency band, when the slow wave structure rotates 90° relative to the parallel plate waveguide, the reflection coefficients corresponding to rotations of the radiating network relative to the feeding network of 0°, 20°, and 40° are as follows: Figure 17 As shown. With the slow-wave structure rotated at a fixed angle of 0° relative to the parallel plate waveguide and the operating frequency at 14 GHz, the normalized radiation patterns of the radiation network rotated relative to the feed network by 0°, 20°, and 40° are shown in the figure. Figure 18 As shown. With the slow-wave structure rotated at a fixed angle of 45° relative to the parallel plate waveguide and the operating frequency at 14.2 GHz, the normalized radiation patterns of the radiation network relative to the feed network at rotations of 0°, 20°, and 40° are shown below. Figure 19 As shown. With the slow-wave structure rotated at a fixed angle of 90° relative to the parallel plate waveguide and the operating frequency at 14.5 GHz, the normalized radiation patterns of the radiation network relative to the feed network at rotations of 0°, 20°, and 40° are shown below. Figure 20 As shown.

[0044] Figures 15 to 20 In the formula, Deg_s represents the rotation angle of the slow wave structure relative to the parallel plate waveguide, and Deg_r represents the rotation angle of the radiation network relative to the feed network.

[0045] Analysis Figure 15 It can be known that when the slow wave structure is rotated by 0° relative to the parallel plate waveguide, and the radiation network is rotated by 0°, 20° and 40° relative to the feed network respectively, the VICTS array antenna of the application always satisfies |S 11 | < -10 dB in the working frequency band of 14-14.5 GHz. Analysis Figure 16 It can be known that when the slow wave structure is rotated by 45° relative to the parallel plate waveguide, and the radiation network is rotated by 0°, 20° and 40° relative to the feed network respectively, the VICTS array antenna of the application always satisfies |S 11 | < -10 dB in the working frequency band of 14-14.5 GHz. Analysis Figure 17 It can be known that when the slow wave structure is rotated by 90° relative to the parallel plate waveguide, and the radiation network is rotated by 0°, 20° and 40° relative to the feed network respectively, |S 11 | < -10 dB in the frequency band of 14-14.5 GHz. It can be known that the VICTS array antenna of the application has good impedance matching, can effectively reduce energy reflection, and can efficiently transmit electromagnetic signals.

[0046] Analysis Figure 18 It can be known that when Deg_s=0° and Deg_r=0° are fixed, the main peak of the beam is accurately directed to 0°, that is, the starting beam of scanning is directed to zero; with the increase of Deg_r to 20° and 40°, the main peak of the beam is synchronously offset to the corresponding angle, and the beam form is stable during the offset process, without obvious abnormal enhancement of sidelobes or distortion of the main peak. The maximum scanning angle is ±60°, and when the scanning angle is 60°, the gain drop is less than 5 dB. It is thus shown that the VICTS array antenna of the application can still maintain good radiation performance in a large scanning range when working at 14 GHz, and can meet the demand of signal strength for long-distance communication.

[0047] Analysis Figure 19It can be seen that when Deg_s=45° and Deg_r=0°, the main peak of the beam is accurately directed to 0°, that is, the scanning starting beam is directed to zero; as Deg_r increases to 20° and 40°, the main peak of the beam is synchronously offset to the corresponding angle, and the beam shape is stable during the offset process, without obvious abnormal enhancement of sidelobes or distortion of the main peak. The maximum scanning angle is ±60°, and when the scanning angle is 60°, the gain drop is less than 5dB. Thus, it is shown that the VICTS array antenna of the application can maintain good radiation performance in a large scanning range when working at 14.2GHz, and meets the demand of long-distance communication for signal strength.

[0048] Analysis Figure 20 It can be seen that when Deg_s=45° and Deg_r=0°, the main peak of the beam is accurately directed to 0°, that is, the scanning starting beam is directed to zero; as Deg_r increases to 20° and 40°, the main peak of the beam is synchronously offset to the corresponding angle, and the beam shape is stable during the offset process, without obvious abnormal enhancement of sidelobes or distortion of the main peak. The maximum scanning angle is ±60°, and when the scanning angle is 60°, the gain drop is less than 5dB. Thus, it is shown that the VICTS array antenna of the application can maintain good radiation performance in a large scanning range when working at 14.2GHz, and meets the demand of long-distance communication for signal strength.

[0049] In summary, the VICTS array antenna of the application can realize large-angle scanning when the overall reflection coefficient |S 11 | is less than-10dB in the working frequency band of 14-14.5GHz, the maximum scanning angle is ±60°, the gain drop is less than 5dB when the scanning angle is 60°, and the scanning starting beam of each frequency point is zero.

Claims

1. A VICTS array antenna scanning a start beam pointing to zero, comprising a feed network and a radiation network; the radiation network comprises a plurality of CTS radiation branches, the plurality of CTS radiation branches are uniformly spaced; the feed network comprises a power division network, a slow wave structure, a parallel plate waveguide and a line source generator; the power division network is used for dividing an externally input TE 10 wave into n paths of TE 10 wave output to the line source generator, n is an integer greater than or equal to 4; the line source generator is used for synthesizing and converting n paths of TE 10 wave into quasi-TEM wave output to the parallel plate waveguide; the slow wave structure is used for coupling with the parallel plate waveguide to change an equivalent guided wave wavelength of the parallel plate waveguide; the parallel plate waveguide is used for transmitting the quasi-TEM wave to the plurality of CTS radiation branches; the plurality of CTS radiation branches are used for radiating the quasi-TEM wave to free space; characterized in that: The slow wave structure is arranged below the parallel plate waveguide, and a gap is arranged between the slow wave structure and the parallel plate waveguide, the gap is not greater than 1mm, the slow wave structure comprises a cylindrical rotating disc and a plurality of pins; the rotating disc is rotatable under force, and the top of the rotating disc is provided with a downwardly recessed curved surface; a plurality of pins are arranged on the curved surface and arranged in the form of multiple rows and multiple columns to form a pin array; the arrangement of the pin array on the curved surface is anisotropic.

2. The VICTS array antenna of claim 1, wherein: The row spacing of the pin array is greater than the column spacing of the pin array.

3. The VICTS array antenna of claim 2, wherein: The power division network has one input end and n output ends; the n output ends of the power division network are distributed in a curve, and the curvature of the curve is equal to the curvature of the curved surface; the line source generator has n input ends and one output end; the n input ends of the line source generator are distributed in a curve, and the curvature of the curve is equal to the curvature of the curved surface; the parallel-plate waveguide has a cuboid structure, and has one input end and one output end; the input end of the power division network is used for accessing externally input TE 10 waves; the n output ends of the power division network are connected to the n input ends of the line source generator one by one, and are used for outputting n paths of TE 10 waves to the n input ends of the line source generator one by one; the output end of the line source generator is connected to the input end of the parallel-plate waveguide, and is used for outputting quasi-TEM waves to the parallel-plate waveguide; and the output end of the parallel-plate waveguide is used for transmitting quasi-TEM waves to a plurality of CTS radiation branches.

4. The VICTS array antenna of claim 3, wherein: n=12, the power division network comprises 7 power dividers, 4 3dB couplers, 8 delay line phase shifters and 8 tapered single-ridge waveguide phase shifters; the 7 power dividers are respectively a first power divider to a seventh power divider; the first power divider is a mirror-symmetrical equal-division power divider; the second power divider to the seventh power divider are all unequal-division power dividers; the 4 3dB couplers are respectively a first 3dB coupler to a fourth 3dB coupler; the 8 delay line phase shifters are respectively a first line phase shifter to an eighth line phase shifter; the 8 tapered single-ridge waveguide phase shifters are respectively a first waveguide phase shifter to an eighth waveguide phase shifter; the first 3dB coupler, the second 3dB coupler, the first line phase shifter, the second line phase shifter, the third line phase shifter, the fourth line phase shifter, the second power divider, the third power divider, the fourth power divider, the first waveguide phase shifter, the second waveguide phase shifter, the third waveguide phase shifter and the fourth waveguide phase shifter constitute a first power division path; the third 3dB coupler, the fourth 3dB coupler, the fifth line phase shifter, the sixth line phase shifter, the seventh line phase shifter, the eighth line phase shifter, the fifth power divider, the sixth power divider, the seventh power divider, the fifth waveguide phase shifter, the sixth waveguide phase shifter, the seventh waveguide phase shifter and the eighth waveguide phase shifter constitute a second power division path; a plane that makes the first power divider mirror-symmetrical is called a symmetry plane, and the second power division path is mirror-symmetrical to the first power division path about the symmetry plane.

5. The VICTS array antenna of claim 4, wherein: Each power divider has an input end, a first output end and a second output end; each 3dB coupler has an input end, a first output end and a second output end; each delay line phase shifter has an input end and an output end; and each tapered single-ridge waveguide phase shifter has an input end and an output end. In the first power division path, the first output end of the first power divider is connected with the input end of the first 3dB coupler, the first output end of the first 3dB coupler is connected with the input end of the first line phase shifter, the output end of the first line phase shifter is connected with the input end of the second 3dB coupler, the first output end of the second 3dB coupler is connected with the input end of the second line phase shifter, the output end of the second line phase shifter is connected with the input end of the first waveguide phase shifter, the second output end of the second 3dB coupler is connected with the input end of the second power divider, the first output end of the second power divider is connected with the input end of the third line phase shifter, the output end of the third line phase shifter is connected with the input end of the second waveguide phase shifter, the second output end of the first 3dB coupler is connected with the input end of the third power divider, the first output end of the third power divider is connected with the input end of the fourth line phase shifter, the output end of the fourth line phase shifter is connected with the input end of the third waveguide phase shifter, the second output end of the third power divider is connected with the input end of the fourth power divider, and the first output end of the fourth power divider is connected with the input end of the fourth waveguide phase shifter.

6. The VICTS array antenna of claim 5, wherein: The third 3dB coupler is mirror-symmetric to the first 3dB coupler about the symmetry plane; the fourth 3dB coupler and the second 3dB coupler are mirror-symmetric about the symmetry plane; the fifth power divider is mirror-symmetric to the second power divider about the symmetry plane; the sixth power divider is mirror-symmetric to the third power divider about the symmetry plane; and the seventh power divider is mirror-symmetric to the fourth power divider about the symmetry plane. The fifth line phase shifter is mirror-symmetric to the first line phase shifter about the symmetry plane. The sixth line phase shifter is mirror-symmetric to the second line phase shifter about the symmetry plane. The seventh line phase shifter is mirror-symmetric to the third line phase shifter about the symmetry plane. The eighth line phase shifter is mirror-symmetric to the fourth line phase shifter about the symmetry plane. The fifth waveguide phase shifter is mirror-symmetric to the first waveguide phase shifter about the symmetry plane; the sixth waveguide phase shifter is mirror-symmetric to the second waveguide phase shifter about the symmetry plane; and the seventh waveguide phase shifter is mirror-symmetric to the third waveguide phase shifter about the symmetry plane. The eighth waveguide phase shifter is mirror-symmetric to the fourth waveguide phase shifter about the symmetry plane; the input end of the first power divider is the input end of the power division network; the output end of the first waveguide phase shifter, the output end of the second waveguide phase shifter, the second output end of the second power divider, the output end of the third waveguide phase shifter, the output end of the fourth waveguide phase shifter, the second output end of the fourth power divider, the second output end of the seventh power divider, the output end of the eighth waveguide phase shifter, the output end of the seventh waveguide phase shifter, the second output end of the fifth power divider, the output end of the sixth waveguide phase shifter, and the output end of the fifth waveguide phase shifter are the twelve output ends of the power division network.

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