6G universal beam domain channel modeling method for full frequency band and full scene

Abstract

The invention discloses a 6G universal beam domain channel modeling method for a full frequency band and a full scene, and relates to the technical field of wireless communication, and the method comprises the steps: 1) setting a frequency band to be modeled and channel parameters corresponding to a scene, determining the antenna configuration and motion trail of a receiving and transmitting end, and generating large-scale and small-scale fading channel parameters; 2) generating a steering vector and a beam offset vector of a transmitting and receiving end, and calculating a channel transmission function of a pervasive geometric random channel model of a spatial domain; 3) generating a pervasive conversion matrix according to the channel parameters, and converting the pervasive geometric random channel model into a pervasive beam domain channel model to obtain a channel transmission function of the pervasive beam domain channel model; 4, channel parameters are updated in real time within the communication time range, and a new beam domain channel transmission function.The method can achieve full-band and full-scene beam domain channel modeling, the complexity of 6G channel simulation can be remarkably reduced, and the method is of great importance to 6G channel model standardization and beam domain channel characteristic research.

Description

Technical Field

[0001] This invention relates to the field of wireless communication technology, and in particular to a 6G universal beam domain channel modeling method for all frequency bands and all scenarios. Background Technology

[0002] With the rapid development of 6G mobile communication system research, the diversity of communication scenarios and frequency bands has greatly increased. 6G is expected to support a full range of communication scenarios, including ultra-large-scale multiple-input multiple-output (MIMO), integrated sensing, high-speed trains, reconfigurable smart metasurfaces, satellite, drones, underground, and marine communication, as well as full-band communication from sub-6 GHz to terahertz and optical wireless bands. Each combination of scenario and frequency band exhibits unique electromagnetic wave propagation characteristics, posing unprecedented challenges to achieving accurate and efficient wireless channel modeling.

[0003] In the research of wireless MIMO propagation channel modeling, geometric random channel models are widely used in different scenarios and frequency bands due to their clear physical meaning and well-defined geometric relationships. However, their main modeling object is the spatial domain channel, which is not only computationally complex but also difficult to effectively characterize the key characteristics in the beam domain. To address these issues, beam domain channel models have gradually attracted attention. Early research mainly focused on far-field conditions, using transformation matrices to convert geometric random channel models to the beam domain for modeling. However, existing beam domain channel modeling methods often rely on specific scenarios or simplified assumptions, making it difficult to achieve unified modeling across all frequency bands and scenarios. Especially under near-field conditions, directly using traditional transformation matrices such as discrete Fourier transforms can easily lead to beam domain sparsity loss and modeling distortion. Although existing methods such as block matrices, near-field steering vector matrices, and polar domain transformation matrices optimize transformation accuracy and applicability from different perspectives, they still suffer from insufficient universality, strong parameter dependence, and computational complexity.

[0004] Therefore, in order to overcome the limitations of existing methods, it is urgent to propose a universal beam domain channel modeling method that can adapt to various scenarios and frequency bands while taking into account both modeling accuracy and computational efficiency, so as to realize a unified representation of the channel in the beam domain. Summary of the Invention

[0005] The technical problem this invention aims to solve is to overcome the shortcomings of existing technologies and provide a 6G universal beam domain channel modeling method applicable to all frequency bands and scenarios. This method describes the channel response in different frequency bands and scenarios in the beam domain, including the spatial broadband effect and spherical wave effect that coexist in ultra-large-scale MIMO communication. This invention will also achieve efficient conversion between universal geometric random channel models and universal beam domain channel models, and significantly reduce the complexity of channel modeling and simulation.

[0006] To solve the above-mentioned technical problems, the present invention adopts the following technical solution:

[0007] A 6G universal beam domain channel modeling method for all frequency bands and scenarios proposed according to the present invention includes:

[0008] Channel parameters are set according to frequency band and scenario to generate channel parameters for large-scale and small-scale fading.

[0009] Generate the steering vector, beam offset vector, antenna response, and multipath delay of the transceiver. Based on the generated steering vector, beam offset vector, antenna response, and multipath delay of the transceiver, calculate the channel transmission function of the universal geometric random channel model in the spatial domain.

[0010] A universal transformation matrix is ​​generated based on the channel parameters. The channel transmission function of the universal geometric random channel model in the spatial domain is then transformed to the beam domain based on the universal transformation matrix to obtain the channel transmission function of the universal beam domain channel model.

[0011] The channel parameters are updated in real time within the communication time range, the spatial domain channel transmission function and universal transformation matrix are recalculated, and a new beam domain channel transmission function is generated.

[0012] As a further optimization of the 6G universal beam domain channel modeling method for all frequency bands and scenarios described in this invention, channel parameters are set according to frequency bands and scenarios to generate channel parameters for large-scale and small-scale fading, including:

[0013] S101, Set the communication frequency band and carrier frequency, transceiver antenna configuration, motion trajectory, scatter cluster parameters, and communication time range;

[0014] S102. Generate large-scale fading channel parameters and the complete channel transfer function matrix of the universal geometric random channel model in the spatial domain. Represented as:

[0015]

[0016] Among them, large-scale fading channel parameters include: free space path loss. Shadow decay Blocking loss Weather-induced attenuation and atmospheric absorption loss ;

[0017] , At carrier frequency The following includes the channel transmission function matrix for both line-of-sight and non-line-of-sight small-scale fading. and These are the number of antennas at the transmitting and receiving ends, respectively. It is the line-of-sight part of the channel transmission function matrix. It is the non-line-of-sight part of the channel transmission function matrix;

[0018] S103. Generate small-scale fading channel parameters and construct the small-scale fading channel transmission function matrix; the universal beam domain channel model adopts multi-hop propagation, defining the elements in the line-of-sight and non-line-of-sight small-scale fading channel transmission function matrices. and , These are elements of the line-of-sight portion of the channel transmission function matrix. These are the elements of the non-line-of-sight portion of the channel transmission function matrix, where... , Represents the coordinate vectors of the transmitting and receiving ends. It is the coordinate vector of the p-th transmitting antenna element. It is the coordinate vector of the q-th receiving antenna element, p=1,2,…, , q=1,2…, , For time variables, For frequency variables; the element in the q-th row and p-th column of the channel transmission function matrix for line-of-sight and non-line-of-sight small-scale fading. , Represented as

[0019]

[0020]

[0021] in, Here, e is the Rice factor, e is the natural constant, and j is the imaginary unit. It is the Doppler frequency of the line-of-sight path between the first transmitting antenna and the first receiving antenna. It is the Doppler frequency of the non-line-of-sight path between the first transmitting antenna and the first receiving antenna. It is the time delay from the first transmitting antenna to the first receiving antenna passing through the m-th scatterer in the n-th cluster. It represents the number of clusters between the p-th transmitting antenna and the q-th receiving antenna. It is the number of scatterers in the nth cluster. It is the power of the m-th ray within the n-th cluster; It is the time delay difference of the line-of-sight path. This is the time delay difference for non-line-of-sight paths. and ;in, It is the time delay from the p-th transmitting antenna to the q-th receiving antenna. It is the time delay of the m-th ray within the n-th cluster;

[0022] This refers to the antenna response at line-of-sight for different azimuth departure and arrival angles, as well as elevation departure and arrival angles. This refers to the antenna response under non-line-of-sight conditions for different azimuth departure angles and angles of arrival, as well as elevation departure angles and angles of arrival.

[0023]

[0024] in It is the matrix transpose. , , , , , Is The initial phase is uniformly distributed within the interior. It is the cross-polarization power ratio. It is a common polarization imbalance. It is a Faraday rotation. It is the antenna response in the vertical direction at the receiving end. It is the antenna response in the horizontal direction at the receiving end. It is the antenna response in the vertical direction at the transmitting end. It is the antenna response in the horizontal direction at the transmitting end;

[0025] , , , These are the azimuth departure angle, azimuth arrival angle, pitch departure angle, and pitch arrival angle of the transceiver at line-of-sight conditions, respectively. , , , These are the azimuth departure angle, azimuth arrival angle, pitch departure angle, and pitch arrival angle, respectively, when passing through the m-th scatterer in the n-th cluster under non-line-of-sight conditions.

[0026] This is a further optimization scheme for the 6G universal beam domain channel modeling method for all frequency bands and all scenarios described in this invention.

[0027] Doppler frequency and Represented as

[0028]

[0029]

[0030] in It's the wavelength. and It refers to the speed of the transmitter and receiver. Represents the vector dot product. It is the Frobenius norm. and These are the coordinates of the scatterer positions of the first and last hops of the nth path. These are the coordinates of the first transmitting antenna element. These are the coordinates of the first receiving antenna element;

[0031] The positions of the antenna elements at the transmitting and receiving ends are represented in the local coordinate system as follows:

[0032]

[0033]

[0034] in, It is the transmitter antenna serial number. It is the tilt vector of the transmitter array. It is the receiver antenna number, It is the receiver array tilt vector. and It is the antenna spacing between the transmitter and receiver, and

[0035]

[0036]

[0037] in It is the azimuth angle of the transmitting end. It is the elevation angle of the transmitter. It is the azimuth angle of the receiving end. It is the elevation angle of the receiving end; during modeling, and According to their respective velocity vectors and Update location.

[0038] As a further optimization of the 6G universal beam domain channel modeling method for all frequency bands and scenarios described in this invention, the channel transmission function of the universal geometric random channel model in the spatial domain is calculated, including:

[0039] S201, Calculate the time delay difference of the line-of-sight portion. The time delay difference between the non-line-of-sight portion Obtain the relationship between the phase differences between antenna elements; define the distance between the p-th transmitting antenna and the q-th receiving antenna as... ;

[0040] Based on the Fresnel approximation, the propagation distance difference between the p-th transmitting antenna and the first transmitting antenna to the first receiving antenna in a line-of-sight scenario, and the propagation distance difference between the first transmitting antenna and the q-th receiving antenna and the first receiving antenna, can be calculated as follows:

[0041]

[0042]

[0043] in, It is the angle between the transmitting antenna array and the line-of-sight path. It is the angle between the receiving antenna array and the line-of-sight path. It is the distance between the first transmitting antenna and the first receiving antenna. , It is the distance between the p-th transmitting antenna and the q-th receiving antenna, and

[0044]

[0045]

[0046] Among them, the azimuth departure angle, azimuth arrival angle, elevation departure angle, and elevation arrival angle are calculated based on the positional relationship between the transmitting and receiving antennas; then, the time delay difference is expressed as two parts at the transmitting end and the receiving end.

[0047]

[0048] Where c is the speed of light. , It is the spatial frequency of the line-of-sight path of the transmitter channel. , It is the spatial frequency of the line-of-sight path at the receiver, and the time delay difference between the transmitter and receiver as the spatial frequency varies. , They are respectively represented as

[0049]

[0050]

[0051] In non-line-of-sight scenarios, the time delay difference between the transmitter and receiver. , Represented as

[0052]

[0053]

[0054] in, , It is the spatial frequency of the non-line-of-sight path of the transmitter channel. , It is the spatial frequency of the non-line-of-sight path of the receiving channel. It is the distance from the first transmitting antenna to the m-th scatterer in the n-th cluster. It is the distance from the first receiving antenna to the m-th scatterer in the n-th cluster;

[0055]

[0056]

[0057] and ;

[0058] in, It is the angle between the transmitting antenna array and the m-th scatterer in the n-th cluster. It is the angle between the receiving antenna array and the m-th scatterer in the n-th cluster;

[0059] S202. Based on the derived time delay difference, reconstruct the channel transmission function matrix in the spatial domain;

[0060] Define the antenna response matrices of the transmitter and receiver as follows:

[0061]

[0062]

[0063] Define the power matrix of rays passing through different scatterers as follows:

[0064]

[0065] in Represents a size of A matrix whose element in row q and column p is the corresponding variable; q = 1, 2, ... p=1,2…, ;

[0066] In step S103, the channel transmission function matrix in the spatial domain is reconstructed as follows:

[0067]

[0068] in, It is Hadamaji. It is the line-of-sight component of the transmitter's steering vector. It is the non-line-of-sight component of the transmitter's steering vector. It is the line-of-sight component of the receiver's steering vector. It is the non-line-of-sight component of the receiver's steering vector. It is the line-of-sight component of the transmitter beam offset vector. It is the non-line-of-sight component of the transmitter beam offset vector. It is the line-of-sight component of the receiver beam offset vector. It is the non-line-of-sight component of the receiver beam offset vector;

[0069]

[0070]

[0071]

[0072]

[0073]

[0074]

[0075]

[0076] .

[0077] As a further optimization of the 6G universal beam domain channel modeling method for all frequency bands and scenarios described in this invention, a universal transformation matrix is ​​generated based on channel parameters. The channel transmission function of the universal geometric random channel model in the spatial domain is then transformed to the beam domain based on the universal transformation matrix, resulting in the channel transmission function of the universal beam domain channel model. This includes:

[0078] S301. Calculate the universal beam domain transformation matrix; beam domain channel transmission function matrix. Represented as

[0079]

[0080] in, It is the conjugate transpose operation. It's a transpose operation. It is the universal transformation matrix at the receiving end. It is the universal transformation matrix of the transmitting end, and

[0081]

[0082]

[0083] in, It is the sampling spatial frequency of the transmitting end. It is the sampling spatial frequency at the receiving end; It is the sampling spatial frequency of the l-th transmitter. The corresponding transmitter steering vector, It is the sampling spatial frequency of the kth receiver. The corresponding receiver steering vector, , ;

[0084] The l-th steering vector at the transmitter and the k-th steering vector at the receiver in the transformation matrix are represented as follows:

[0085]

[0086]

[0087] It is the sampling spatial frequency of the l-th transmitter. The corresponding time delay difference, It is the sampling spatial frequency of the kth receiver. The corresponding time delay difference; and the time delay difference in the channel transfer function. , , , In contrast, the time delay difference in the universal transformation matrix no longer distinguishes between line-of-sight and non-line-of-sight cases, therefore the subscript is omitted. and ;

[0088] To ensure the transformation matrix is ​​unitary, the time delay difference is further adjusted to...

[0089]

[0090]

[0091] in, and These are the angular distance loop parameters for the transmitter and receiver, respectively, and their values ​​will be calculated based on the near-field and far-field conditions of the channel.

[0092]

[0093]

[0094] in, , It is the average spatial frequency of the transmitter and receiver. , It is the average transmission distance between the transmitter and receiver; for far-field conditions, ;

[0095] The sampling spatial frequency of the transmitter and receiver is expressed as:

[0096]

[0097]

[0098] Its relationship with the actual physical perspective is as follows:

[0099]

[0100]

[0101] Similar to the time delay difference, the azimuth departure angle is... Pitch departure angle azimuth arrival angle Angle of arrival at pitch It also includes both line-of-sight and non-line-of-sight scenarios;

[0102] S302. Based on the universal beam domain transformation matrix and the reconstructed spatial domain channel transmission function matrix in step S202, the channel transmission function in the beam domain is obtained.

[0103] The k-th row and l-th column of the channel transmission function matrix in the beam domain Represented as

[0104]

[0105] in, It is a beam domain channel transmission function that includes line-of-sight components. and non-line-of-sight components ;

[0106] The line-of-sight and non-line-of-sight components are further expressed as:

[0107]

[0108] in, , This represents the normalized direction vectors of the transmitted and received beams. It is the first One transmission beam, It is the first The normalized direction vector of each receiving beam. and These represent the beam divisions at the transmitting and receiving ends, respectively, encompassing frequencies close to the sampling spatial frequency. and The set of paths; the double summation symbol in the two formulas for line-of-sight and non-line-of-sight components indicates that when the corresponding line-of-sight or non-line-of-sight path falls within the defined beam division, its contribution to the corresponding element of the beam domain channel matrix will be included.

[0109] As a further optimization of the 6G universal beam domain channel modeling method for all frequency bands and scenarios described in this invention, the channel parameters are updated in real time within the communication time range, the spatial domain channel transmission function and universal transformation matrix are recalculated, and a new beam domain channel transmission function is generated; including:

[0110] S401. Based on velocity and birth-death probability parameters, generate the real-time position and multipath power changes of the transmitter, receiver and scattering cluster within the simulation time, and calculate the new spatial domain channel transmission function matrix.

[0111] S402. Calculate the new steering vector and beam offset vector based on the spatial domain channel transmission function matrix;

[0112] S403. Construct a new universal transformation matrix based on the steering vector and beam offset vector;

[0113] S404. Calculate the new beam domain channel transmission function matrix based on the spatial domain channel transmission function matrix and the universal transformation matrix.

[0114] Compared with the prior art, the present invention, employing the above technical solution, has the following technical effects:

[0115] This invention proposes a universal 6G beamdomain channel modeling method applicable to all frequency bands and scenarios. Based on the proposed universal transformation matrix suitable for different antenna array configurations, the method achieves mutual conversion between the universal geometric random channel model and the universal beamdomain channel model under near-field and far-field conditions. Compared with the traditional discrete Fourier transform matrix, the universal transformation matrix under near-field conditions can concentrate beam energy within a smaller range, thereby enhancing the sparsity of the beamdomain channel. Furthermore, the computational complexity of the universal beamdomain channel model is significantly lower than that of the universal geometric random channel model. This invention provides an efficient and universal method for beamdomain channel modeling in different frequency bands and scenarios, which will provide strong support for promoting the development of future signal processing and wireless communication system design. Attached Figure Description

[0116] Figure 1 This is a flowchart of the method of the present invention;

[0117] Figure 2 This is a schematic diagram of the 6G universal beam domain channel model in this invention;

[0118] Figure 3 The diagram shows a comparison of near-field normalized beam domain channel power obtained using different transformation matrices in Embodiment 1 of the present invention, where (a) uses the discrete Fourier transform matrix and (b) uses the universal transformation matrix.

[0119] Figure 4The diagram shows a comparison of the normalized beam domain channel power obtained with and without considering the spatial broadband effect in Embodiment 1 of the present invention, where (a) represents the power without considering the spatial broadband effect and (b) represents the power with considering the spatial broadband effect.

[0120] Figure 5 This refers to the computational complexity of the universal beam domain channel model and the corresponding universal geometric random channel model in Embodiment 1 of the present invention under different scatterer densities. Detailed Implementation

[0121] To make the objectives, technical solutions, and advantages of this invention clearer, the invention will be described in detail below with reference to the accompanying drawings and specific embodiments.

[0122] Example 1:

[0123] See Figure 1 This embodiment provides a universal beam domain channel modeling method, which specifically includes the following steps:

[0124] Step S1: Set channel parameters according to frequency band and scenario to generate large-scale and small-scale fading channel parameters.

[0125] Specifically, in this embodiment, step 1 includes:

[0126] S101. Set basic parameters such as communication frequency band and carrier frequency, transceiver antenna configuration, motion trajectory, scattering cluster parameters, and communication time range.

[0127] S102. Generate large-scale fading channel parameters. Complete channel transfer function matrix of the universal geometrical random channel model in the spatial domain. Represented as:

[0128]

[0129] Large-scale fading channel parameters include It is free space path loss. It is the decline of shadows. It is to prevent loss. The decline is due to weather conditions. This refers to atmospheric absorption loss; the calculation of this part can be referenced from the 6G ubiquitous channel model. At carrier frequency The following is a channel transmission function matrix containing line-of-sight and non-line-of-sight small-scale fading, where and These refer to the number of antennas at the transmitting and receiving ends, respectively.

[0130] S103. Generate small-scale fading channel parameters and construct the small-scale fading channel transmission function matrix. A schematic diagram of the universal beam domain channel model is shown below. Figure 2The elements in the transmission function matrix of line-of-sight and non-line-of-sight small-scale fading channels are defined as follows: and ,in Represents the coordinate vectors of the transmitting and receiving ends. For time variables, For frequency variables, the elements in the q-th row and p-th column of the channel transmission function matrix for line-of-sight and non-line-of-sight small-scale fading can be represented as follows:

[0131]

[0132] in, Here, e is the Rice factor, e is the natural constant, and j is the imaginary unit. It is the Doppler frequency of the line-of-sight path between the first transmitting antenna and the first receiving antenna. It is the Doppler frequency of the non-line-of-sight path between the first transmitting antenna and the first receiving antenna. It is the time delay from the first transmitting antenna to the first receiving antenna passing through the m-th scatterer in the n-th cluster. It represents the number of clusters between the p-th transmitting antenna and the q-th receiving antenna. It is the number of scatterers in the nth cluster. It is the power of the m-th ray within the n-th cluster; It is the time delay difference of the line-of-sight path. This is the time delay difference for non-line-of-sight paths. and ;in, It is the time delay from the p-th transmitting antenna to the q-th receiving antenna. It is the time delay of the m-th ray within the n-th cluster;

[0133] This refers to the antenna response at line-of-sight for different azimuth departure and arrival angles, as well as elevation departure and arrival angles. This refers to the antenna response under non-line-of-sight conditions for different azimuth departure angles and angles of arrival, as well as elevation departure angles and angles of arrival.

[0134]

[0135] in It is the matrix transpose. , , , , , Is The initial phase is uniformly distributed within the interior. It is the cross-polarization power ratio. It is a common polarization imbalance. It is a Faraday rotation. It is the antenna response in the vertical direction at the receiving end. It is the antenna response in the horizontal direction at the receiving end. It is the antenna response in the vertical direction at the transmitting end. It is the antenna response in the horizontal direction at the transmitting end;

[0136] , , , These are the azimuth departure angle, azimuth arrival angle, pitch departure angle, and pitch arrival angle of the transceiver at line-of-sight conditions, respectively. , , , These are the azimuth departure angle, azimuth arrival angle, pitch departure angle, and pitch arrival angle, respectively, when passing through the m-th scatterer in the n-th cluster under non-line-of-sight conditions.

[0137] Doppler frequency and It can be represented as

[0138]

[0139]

[0140] in It's the wavelength. and It refers to the speed of the transmitter and receiver. Represents the vector dot product. It is the Frobenius norm. and These are the positions of the first and last hop scatterers on the nth path. The antenna element positions at the transmitter and receiver can be represented in the local coordinate system as follows:

[0141]

[0142]

[0143] in, It is the transmitter antenna serial number. It is the tilt vector of the transmitter array. It is the receiver antenna number, It is the receiver array tilt vector. and It is the antenna spacing between the transmitter and receiver, and

[0144]

[0145]

[0146] in It is the azimuth angle of the transmitting end. It is the elevation angle of the transmitter. It is the azimuth angle of the receiving end. It is the elevation angle of the receiving end; during modeling, and According to their respective velocity vectors and Update location.

[0147] Step S2: Generate the steering vector and beam offset vector of the transceiver, and calculate the channel transmission function of the universal geometric random channel model in the spatial domain.

[0148] Specifically, in this embodiment, step 2 includes:

[0149] S201, Calculate the time delay difference of the line-of-sight portion. The time delay difference between the non-line-of-sight portion Obtain the relationship between the phase differences between antenna elements; define the distance between the p-th transmitting antenna and the q-th receiving antenna as... ;

[0150] Based on the Fresnel approximation, the propagation distance difference between the p-th transmitting antenna and the first transmitting antenna to the first receiving antenna in a line-of-sight scenario, and the propagation distance difference between the first transmitting antenna and the q-th receiving antenna and the first receiving antenna, can be calculated as follows:

[0151]

[0152]

[0153] in, It is the angle between the transmitting antenna array and the line-of-sight path. It is the angle between the receiving antenna array and the line-of-sight path. It is the distance between the first transmitting antenna and the first receiving antenna. , It is the distance between the p-th transmitting antenna and the q-th receiving antenna, and

[0154]

[0155]

[0156] Among them, the azimuth departure angle, azimuth arrival angle, elevation departure angle, and elevation arrival angle are calculated based on the positional relationship between the transmitting and receiving antennas; then, the time delay difference is expressed as two parts at the transmitting end and the receiving end.

[0157]

[0158] Where c is the speed of light. It is the spatial frequency of the line-of-sight path of the transmitter channel. This is the spatial frequency of the line-of-sight path at the receiver. The time delay difference between the transmitter and receiver as a function of spatial frequency is expressed as follows:

[0159]

[0160]

[0161] In non-line-of-sight scenarios, the time delay difference between the transmitter and receiver can be expressed in a similar manner as follows:

[0162]

[0163]

[0164] in It is the spatial frequency of the non-line-of-sight path of the transmitter channel. Spatial frequency of the non-line-of-sight path of the receiver channel.

[0165]

[0166]

[0167] and .

[0168] S202. Based on the derived time delay difference, reconstruct the channel transmission function matrix in the spatial domain. The channel transmission function matrix in the spatial domain in step S103 can be reconstructed as follows:

[0169]

[0170] in, It is Hadamaji. It is the line-of-sight component of the transmitter's steering vector. It is the non-line-of-sight component of the transmitter's steering vector. It is the line-of-sight component of the receiver's steering vector. It is the non-line-of-sight component of the receiver's steering vector. It is the line-of-sight component of the transmitter beam offset vector. It is the non-line-of-sight component of the transmitter beam offset vector. It is the line-of-sight component of the receiver beam offset vector. It is the non-line-of-sight component of the receiver beam offset vector;

[0171]

[0172]

[0173]

[0174]

[0175]

[0176]

[0177]

[0178] .

[0179] The steering vector and beam offset vector can be used to characterize the near-field spherical wavefront effect and the spatial broadband effect, respectively. The spherical wavefront effect refers to the nonlinear phase difference between adjacent antenna elements under near-field transmission conditions; while the spatial broadband effect refers to the nonlinear phase difference between different antenna elements at different frequencies. The fundamental cause of these two effects lies in the transmission signal delay difference caused by large-scale antenna arrays. When far-field conditions are met, the spherical wavefront effect can be ignored; and when only narrowband channels are considered, the spatial broadband effect will no longer appear.

[0180] Step S3: Generate a universal transformation matrix based on the channel parameters, and convert the universal geometric random channel model into a universal beam domain channel model to obtain the channel transmission function of the universal beam domain channel model.

[0181] Specifically, in this embodiment, step 3 includes:

[0182] S301. Calculate the universal beam domain transformation matrix. Beam domain channel transmission function matrix. It can be represented as

[0183]

[0184] in It is the conjugate transpose operation. It is the transpose operation, and

[0185]

[0186]

[0187] This is the universal transformation matrix for both the transmitter and receiver. The steering vector in the transformation matrix can be represented as...

[0188]

[0189]

[0190] The time delay difference includes both line-of-sight and non-line-of-sight components, therefore its subscripts have been simplified. To ensure the transformation matrix is ​​unitary, the time delay difference is further adjusted to...

[0191]

[0192]

[0193] in and These are the angular range loop parameters for the transmitter and receiver, respectively. Their values ​​are calculated based on the near-field and far-field conditions of the channel, specifically expressed as follows:

[0194]

[0195]

[0196] in, , It is the average spatial frequency of the transmitter and receiver. , It is the average transmission distance between the transmitter and receiver; for far-field conditions, ;

[0197] The sampling spatial frequency of the transmitter and receiver is expressed as:

[0198]

[0199]

[0200] Its relationship with the actual physical perspective is as follows:

[0201]

[0202]

[0203] S302. Based on the universal beam domain transformation matrix and the reconstructed spatial domain channel transmission function matrix in step S202, the channel transmission function in the beam domain is obtained. The channel transmission function in the beam domain can be expressed as:

[0204]

[0205] The specific line-of-sight and non-line-of-sight components are represented as follows:

[0206]

[0207] in, , This represents the normalized direction vectors of the transmitted and received beams. It is the first One transmission beam, It is the first The normalized direction vector of each receiving beam. and These represent the beam divisions at the transmitting and receiving ends, respectively, encompassing frequencies close to the sampling spatial frequency. and The path set; the double summation symbol in the two formulas for line-of-sight and non-line-of-sight components indicates that when the corresponding line-of-sight or non-line-of-sight path falls within the defined beam division, its contribution to the corresponding element of the beam domain channel matrix will be included. It should be noted that although this method assumes the use of a uniform linear array, the proposed universal transformation matrix is ​​also applicable to uniform area arrays, because a uniform area array can be viewed as a combination of two orthogonal uniform linear arrays. The steering vector of the uniform area array can be constructed by the Kronecker product of the steering vectors of the two uniform linear arrays in the vertical and horizontal directions, corresponding to the elevation and azimuth resolutions of the uniform area array, respectively.

[0208] Step S4: Update the channel parameters in real time within the communication time range to generate a new beam domain channel transmission function.

[0209] Specifically, in this embodiment, step 4 includes:

[0210] S401. Based on velocity and birth-death probability parameters, generate the real-time position and multipath power changes of the transmitter, receiver and scattering cluster within the simulation time, and calculate the new spatial domain channel transmission function matrix.

[0211] S402. Calculate the new steering vector and beam offset vector based on the spatial domain channel transmission function matrix;

[0212] S403. Construct a new universal transformation matrix based on the steering vector and beam offset vector;

[0213] S404. Based on the spatial domain channel transmission function matrix and the universal transformation matrix, calculate the new beam domain channel transmission function matrix;

[0214] S405. Update the beam domain channel transmission function matrix.

[0215] Figure 3The simulation results of normalized channel power obtained using the discrete Fourier transform matrix and the universal transform matrix are presented when the distance between the transmitter and receiver is less than the Rayleigh distance of the transmit antenna array, i.e., the receiver is in the near field of the transmitter. Figure 3 (a) and Figure 3 As can be seen in (b), the universal transformation matrix can concentrate beam energy within a narrower range, thereby improving the sparsity of the beam domain channel. This improvement stems from the fact that the proposed universal transformation matrix takes into account the distance between the transmitter and receiver, and therefore can more effectively resolve near-field beams compared to the discrete Fourier transform matrix that only considers beam angles in different directions.

[0216] Figure 4 The impact of spatial broadband effects on the beam domain channel matrix is ​​demonstrated. Figure 4 Figure (a) shows the normalized channel power without considering spatial broadband effects, clearly distinguishing a dominant line-of-sight path and three non-line-of-sight paths, with their energy distributed along different beam directions. The results show that the beam direction remains constant with frequency variations. In contrast, Figure 4 Figure (b) shows the normalized channel power considering the spatial broadband effect. It can be observed that the beam direction shifts to some extent with frequency. This phenomenon is due to the frequency-dependent phase difference in large-scale antenna arrays, which causes the beam direction to change at different frequencies.

[0217] Based on the derived spatial and beam domain channel transmission function matrix expressions and the concept of real operations (RO), the computational complexity of the universal geometric random channel model and the universal beam domain channel model is analyzed below. The number of real operations required to generate the geometric random channel model is discussed. It can be represented as

[0218] Among them, the line-of-sight component is treated as a special path of the non-line-of-sight component. This represents the number of real computations required for the response of each ray channel between each pair of single antennas. This represents the number of ROs required to generate the antenna response matrix. This represents the number of ROs required to generate each element in the steering vector and beam offset vector. Based on the reconstructed spatial domain channel transmission function matrix obtained in step S2, the operations required to calculate the channel response for each pair of antennas include: 6 multiplication and division operations (6 ROs), 1 real number square root operation (1 RO), 1 addition operation (1 RO), 1 exponentiation operation (15 ROs), and 1 assignment operation (1 RO). The number of operations required to generate the antenna response matrix depends on the antenna array configuration at both the transmitter and receiver. For each pair of antennas, at most three two-dimensional matrix multiplication operations are involved (a total of six ROs). This can be further simplified if the array elements have similar antenna patterns. Therefore: The operations required to generate each element of the steering vector and beam offset vector include: 1 coordinate vector subtraction (3 ROs), 1 modulo operation (6 ROs), 9 multiplications and divisions (9 ROs), 1 addition (1 RO), and 1 assignment operation (1 RO). Therefore: Furthermore, to generate the corresponding steering matrix and beam offset matrix, it is also necessary to perform a process with dimension [missing information]. and Complex vector multiplication requires a total of One RO. Finally, the combination process of the channel transfer function matrix includes two Hadamard product operations (requiring a total of...). One RO and one multiplication operation (1 RO).

[0219] The complexity of the proposed universal beam domain channel model It can be calculated as

[0220]

[0221] in, This represents the number of ROs required to generate a beam domain channel response between beam division pairs. This represents the number of Representations (ROs) required to generate the antenna response matrix. Considering the sparsity of the BDCM, the overall number of ROs required can be significantly reduced. For generating the beam domain channel response between a single beam pair, the required operations include: 1 coordinate vector subtraction (3 ROs), 1 modulus operation (6 ROs), 2 mapping operations (8 ROs), 10 multiplication and division operations (10 ROs), 1 real square root operation (1 RO), 1 exponentiation operation (15 ROs), 1 addition operation (1 RO), and 1 assignment operation (1 RO). When the same antenna array is used at both the transmitting and receiving ends, the number of operations required to generate the antenna response matrix remains unchanged, i.e. .

[0222] Figure 5This paper presents the complexity of the universal beamdomain channel model and the universal geometric random channel model under different scattering environments. The results show that the complexity of the universal beamdomain channel model is significantly lower than that of the universal geometric random channel model as the number of transmitter antenna elements increases. Furthermore, the complexity of the universal beamdomain channel model also decreases as the number of scatterers decreases. This is because the fewer transmit and receive beams in sparse scattering environments allow the universal beamdomain channel model to better utilize its sparsity. Conversely, increasing the number of scatterers leads to an increase in beams and a decrease in channel sparsity. On the other hand, the complexity of the universal geometric random channel model is less affected by the number of scatterers because it considers the influence of all scattering paths between each pair of transmit and receive antennas. When the number of antenna elements in a large-scale MIMO system is large, the influence of additional scatterers can be ignored. However, when the number of transmitter antenna elements is small, an increase in the number of scatterers leads to an increase in the complexity of the universal geometric random channel model.

[0223] Any aspects of this invention not described in detail are well-known to those skilled in the art.

[0224] The above description is merely a specific embodiment of the present invention, but the scope of protection of the present invention is not limited thereto. Any variations or substitutions that can be easily conceived by those skilled in the art within the scope of the technology disclosed in the present invention should be included within the scope of protection of the present invention.

Claims

1. A 6G universal beam domain channel modeling method for all frequency bands and scenarios, characterized in that, include: Channel parameters are set according to frequency band and scenario to generate channel parameters for large-scale and small-scale fading. Generate the steering vector, beam offset vector, antenna response, and multipath delay of the transceiver. Based on the generated steering vector, beam offset vector, antenna response, and multipath delay of the transceiver, calculate the channel transmission function of the universal geometric random channel model in the spatial domain. A universal transformation matrix is ​​generated based on the channel parameters. The channel transmission function of the universal geometric random channel model in the spatial domain is then transformed to the beam domain based on the universal transformation matrix to obtain the channel transmission function of the universal beam domain channel model. The channel parameters are updated in real time within the communication time range, the spatial domain channel transmission function and universal transformation matrix are recalculated, and a new beam domain channel transmission function is generated.

2. The 6G universal beam domain channel modeling method for all frequency bands and scenarios according to claim 1, characterized in that, Channel parameters are set according to frequency band and scenario to generate channel parameters for large-scale and small-scale fading, including: S101, Set the communication frequency band and carrier frequency, transceiver antenna configuration, motion trajectory, scatter cluster parameters, and communication time range; S102. Generate large-scale fading channel parameters and the complete channel transfer function matrix of the universal geometric random channel model in the spatial domain. Represented as: ； Among them, large-scale fading channel parameters include: free space path loss. Shadow decay Blocking loss Weather-induced attenuation and atmospheric absorption loss ; , At carrier frequency The following includes the channel transmission function matrix for both line-of-sight and non-line-of-sight small-scale fading. and These are the number of antennas at the transmitting and receiving ends, respectively. It is the line-of-sight part of the channel transmission function matrix. It is the non-line-of-sight part of the channel transmission function matrix; S103. Generate small-scale fading channel parameters and construct the small-scale fading channel transmission function matrix; the universal beam domain channel model adopts multi-hop propagation, defining the elements in the line-of-sight and non-line-of-sight small-scale fading channel transmission function matrices. and , These are elements of the line-of-sight portion of the channel transmission function matrix. These are the elements of the non-line-of-sight portion of the channel transmission function matrix, where... , Represents the coordinate vectors of the transmitting and receiving ends. It is the coordinate vector of the p-th transmitting antenna element. It is the coordinate vector of the q-th receiving antenna element, p=1,2,…, , q=1,2…, , For time variables, For frequency variables; the element in the q-th row and p-th column of the channel transmission function matrix for line-of-sight and non-line-of-sight small-scale fading. , Represented as ； ； in, Here, e is the Rice factor, e is the natural constant, and j is the imaginary unit. It is the Doppler frequency of the line-of-sight path between the first transmitting antenna and the first receiving antenna. It is the Doppler frequency of the non-line-of-sight path between the first transmitting antenna and the first receiving antenna. It is the time delay from the first transmitting antenna to the first receiving antenna passing through the m-th scatterer in the n-th cluster. It represents the number of clusters between the p-th transmitting antenna and the q-th receiving antenna. It is the number of scatterers in the nth cluster. It is the power of the m-th ray within the n-th cluster; It is the time delay difference of the line-of-sight path. This is the time delay difference for non-line-of-sight paths. and ;in, It is the time delay from the p-th transmitting antenna to the q-th receiving antenna. It is the time delay of the m-th ray within the n-th cluster; This refers to the antenna response at line-of-sight for different azimuth departure and arrival angles, as well as elevation departure and arrival angles. This refers to the antenna response under non-line-of-sight conditions for different azimuth departure angles and angles of arrival, as well as elevation departure angles and angles of arrival. ； ;in It is the matrix transpose. , , , , , Is The initial phase is uniformly distributed within the interior. It is the cross-polarization power ratio. It is a common polarization imbalance. It is a Faraday rotation. It is the antenna response in the vertical direction at the receiving end. It is the antenna response in the horizontal direction at the receiving end. It is the antenna response in the vertical direction at the transmitting end. It is the antenna response in the horizontal direction at the transmitting end; , , , These are the azimuth departure angle, azimuth arrival angle, pitch departure angle, and pitch arrival angle of the transceiver at line-of-sight conditions, respectively. , , , These are the azimuth departure angle, azimuth arrival angle, pitch departure angle, and pitch arrival angle, respectively, when passing through the m-th scatterer in the n-th cluster under non-line-of-sight conditions.

3. The 6G universal beam domain channel modeling method for all frequency bands and scenarios according to claim 2, characterized in that, Doppler frequency and Represented as ； ； in It's the wavelength. and It refers to the speed of the transmitter and receiver. Represents the vector dot product. It is the Frobenius norm. and These are the coordinates of the scatterer positions of the first and last hops of the nth path. These are the coordinates of the first transmitting antenna element. These are the coordinates of the first receiving antenna element; The positions of the antenna elements at the transmitting and receiving ends are represented in the local coordinate system as follows: ； ； in, It is the transmitter antenna serial number. It is the tilt vector of the transmitter array. It is the receiver antenna number, It is the receiver array tilt vector. and It is the antenna spacing between the transmitter and receiver, and ； ； in It is the azimuth angle of the transmitting end. It is the elevation angle of the transmitter. It is the azimuth angle of the receiving end. It is the elevation angle of the receiving end; during modeling, and According to their respective velocity vectors and Update location.

4. The 6G universal beam domain channel modeling method for all frequency bands and scenarios according to claim 2, characterized in that, The channel transfer function of a universal geometric random channel model in the computational space domain includes: S201, Calculate the time delay difference of the line-of-sight portion. The time delay difference between the non-line-of-sight portion Obtain the relationship between the phase differences between antenna elements; define the distance between the p-th transmitting antenna and the q-th receiving antenna as... ; Based on the Fresnel approximation, the propagation distance difference between the p-th transmitting antenna and the first transmitting antenna to the first receiving antenna in a line-of-sight scenario, and the propagation distance difference between the first transmitting antenna and the q-th receiving antenna and the first receiving antenna, can be calculated as follows: ； ； in, It is the angle between the transmitting antenna array and the line-of-sight path. It is the angle between the receiving antenna array and the line-of-sight path. It is the distance between the first transmitting antenna and the first receiving antenna. , It is the distance between the p-th transmitting antenna and the q-th receiving antenna, and ； ； Among them, the azimuth departure angle, azimuth arrival angle, elevation departure angle, and elevation arrival angle are calculated based on the positional relationship between the transmitting and receiving antennas; then, the time delay difference is expressed as two parts at the transmitting end and the receiving end. ； Where c is the speed of light. , It is the spatial frequency of the line-of-sight path of the transmitter channel. , It is the spatial frequency of the line-of-sight path at the receiver, and the time delay difference between the transmitter and receiver as the spatial frequency varies. , They are respectively represented as ； ； In non-line-of-sight scenarios, the time delay difference between the transmitter and receiver. , Represented as ； ； in, , It is the spatial frequency of the non-line-of-sight path of the transmitter channel. , It is the spatial frequency of the non-line-of-sight path of the receiving channel. It is the distance from the first transmitting antenna to the m-th scatterer in the n-th cluster. It is the distance from the first receiving antenna to the m-th scatterer in the n-th cluster; ； ； and ; in, It is the angle between the transmitting antenna array and the m-th scatterer in the n-th cluster. It is the angle between the receiving antenna array and the m-th scatterer in the n-th cluster; S202. Based on the derived time delay difference, reconstruct the channel transmission function matrix in the spatial domain; Define the antenna response matrices of the transmitter and receiver as follows: ； ； Define the power matrix of rays passing through different scatterers as follows: ； in Represents a size of A matrix whose element in row q and column p is the corresponding variable; q = 1, 2, ... p=1,2…, ; In step S103, the channel transmission function matrix in the spatial domain is reconstructed as follows: ； ； in, It is Hadamaji. It is the line-of-sight component of the transmitter's steering vector. It is the non-line-of-sight component of the transmitter's steering vector. It is the line-of-sight component of the receiver's steering vector. It is the non-line-of-sight component of the receiver's steering vector. It is the line-of-sight component of the transmitter beam offset vector. It is the non-line-of-sight component of the transmitter beam offset vector. It is the line-of-sight component of the receiver beam offset vector. It is the non-line-of-sight component of the receiver beam offset vector; ； ； ； ； ； ； ； 。 5. The 6G universal beam domain channel modeling method for all frequency bands and scenarios according to claim 1, characterized in that, A universal transformation matrix is ​​generated based on the channel parameters. Using this universal transformation matrix, the channel transmission function of the universal geometric random channel model in the spatial domain is transformed to the beam domain, resulting in the channel transmission function of the universal beam domain channel model; including: S301. Calculate the universal beam domain transformation matrix; beam domain channel transmission function matrix. Represented as ； in, It is the conjugate transpose operation. It's a transpose operation. It is the universal transformation matrix at the receiving end. It is the universal transformation matrix of the transmitting end, and ； ； in, It is the sampling spatial frequency of the transmitting end. It is the sampling spatial frequency at the receiving end; It is the sampling spatial frequency of the l-th transmitter. The corresponding transmitter steering vector, It is the sampling spatial frequency of the kth receiver. The corresponding receiver steering vector, , ; The l-th steering vector at the transmitter and the k-th steering vector at the receiver in the transformation matrix are represented as follows: ； ； It is the sampling spatial frequency of the l-th transmitter. The corresponding time delay difference, It is the sampling spatial frequency of the kth receiver. The corresponding time delay difference; and the time delay difference in the channel transfer function. , , , In contrast, the time delay difference in the universal transformation matrix no longer distinguishes between line-of-sight and non-line-of-sight cases, therefore the subscript is omitted. and ; To ensure the transformation matrix is ​​unitary, the time delay difference is further adjusted to... ； ； in, and These are the angular distance loop parameters for the transmitter and receiver, respectively, and their values ​​will be calculated based on the near-field and far-field conditions of the channel. ； ； in, , It is the average spatial frequency of the transmitter and receiver. , It is the average transmission distance between the transmitter and receiver; for far-field conditions, ; The sampling spatial frequency of the transmitter and receiver is expressed as: ； ； Its relationship with the actual physical perspective is as follows: ； ； Similar to the time delay difference, the azimuth departure angle is... Pitch departure angle azimuth arrival angle Angle of arrival at pitch It also includes both line-of-sight and non-line-of-sight scenarios; S302. Based on the universal beam domain transformation matrix and the reconstructed spatial domain channel transmission function matrix in step S202, the channel transmission function in the beam domain is obtained. The k-th row and l-th column of the channel transmission function matrix in the beam domain Represented as ； in, It is a beam domain channel transmission function that includes line-of-sight components. and non-line-of-sight components ; The line-of-sight and non-line-of-sight components are further expressed as: ； ;in, , This represents the normalized direction vectors of the transmitted and received beams. It is the first One transmission beam, It is the first The normalized direction vector of each receiving beam. and These represent the beam divisions at the transmitting and receiving ends, respectively, encompassing frequencies close to the sampling spatial frequency. and The set of paths; the double summation symbol in the two formulas for line-of-sight and non-line-of-sight components indicates that when the corresponding line-of-sight or non-line-of-sight path falls within the defined beam division, its contribution to the corresponding element of the beam domain channel matrix will be included.

6. The 6G universal beam domain channel modeling method for all frequency bands and scenarios according to claim 1, characterized in that, The channel parameters are updated in real time within the communication time range, the spatial domain channel transmission function and universal transformation matrix are recalculated, and a new beam domain channel transmission function is generated; including: S401. Based on velocity and birth-death probability parameters, generate the real-time position and multipath power changes of the transmitter, receiver and scattering cluster within the simulation time, and calculate the new spatial domain channel transmission function matrix. S402. Calculate the new steering vector and beam offset vector based on the spatial domain channel transmission function matrix; S403. Construct a new universal transformation matrix based on the steering vector and beam offset vector; S404. Calculate the new beam domain channel transmission function matrix based on the spatial domain channel transmission function matrix and the universal transformation matrix.

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