ROTARY ELECTRIC MACHINE CONTROL DEVICE

Abstract

To propose a rotating electric machine control device capable of estimating the applied voltages commonly applied to the armature windings during the execution of alternator generation control, when the multi-phase armature windings of two sets are provided.A rotating electric machine control device (30) which controls a rotating electric machine (1) having m-phase armature windings of a first set and m-phase armature windings of a second set, the rotating electric machine control device (30) calculates estimation values ​​of applied voltages currently applied to the armature windings of each set, on the basis of detection values ​​of current flowing in the armature windings of each set when alternator generation control is executed; and, in each set, a phase angle difference between the armature windings of the first set and the armature windings of the second set is equal to 1 / 2 of the minimum phase angle difference (Δθmin) among the phases of each set.

Description

Title of the invention: ROTARY ELECTRIC MACHINE CONTROL DEVICE

[0001] CONTEXT

[0002] The present disclosure relates to a device for controlling a rotating electrical machine.

[0003]

[0002] In the multi-winding motor of patent document 1, by calculating the non-interference voltages based on the d-axis current instruction value, the q-axis current instruction value, the resistance, the inductance, the magnetic flux and the electric angle velocity, the non-interaction control is realized in the multiple windings, and the current control response is improved.

[0004]

[0003] In the AC rotating machine control device of patent document 2, since the current instruction values ​​of the armature winding are not calculated in the alternator generation control, when switching from the alternator generation control to the inverter control, the current detection values ​​are used instead of the previous current instruction values; and the basic voltage instruction values ​​are calculated based on the present current instruction values, the current detection values, and the electrical constants of the AC rotating machine. Therefore, the accuracy of the voltage instruction values ​​at the time of starting the inverter control is improved, and the variation of the bus current is suppressed.

[0005]

[0004] Patent Document 1: JP H11-262293 A Patent document 2: JP 7002625 B

[0006] SUMMARY

[0007]

[0005] In the case where the interference-free voltages are calculated as in patent document 1, if the resistance, inductance and magnetic flux are given with good accuracy, the interference-free voltages become equivalent to voltages required to output the current instruction values ​​in the steady state. However, in practice, due to production variation, temperature change, aging change and the like, the voltage instruction values ​​in the steady state are different from the interference-free voltages. interference. This means that even though the applied voltages are obtained using the equation for calculating interference-free voltages from the excitation currents, the applied voltages deviate from the actual applied voltages.

[0008]

[0006] The basic voltage instruction values ​​obtained in Patent Document 2 are calculated based on the current detection values ​​at the time of alternator generation control, the current instruction values, and the electrical constants of the AC rotating machine. However, the accuracy is reduced due to the error of the electrical constants. Since synchronous rectification or diode rectification is performed at the time of alternator generation control, the voltage instruction values ​​are not calculated as in the case of inverter control, and the voltages applied to the armature winding cannot be acquired.For example, if there is an error of the base voltage instruction values ​​due to the error of the electrical constants, when switching from the alternator generation control to the inverter control, the deviation between the voltages applied just before the end of the alternator generation control and the base voltage instruction values ​​becomes large, and the variation of the bus current may become large.

[0009]

[0007] The objective of the present disclosure is to provide a rotating electric machine control device capable of estimating the applied voltages commonly applied to the armature windings during the execution of alternator generation control, when the multi-phase armature windings of two sets are provided.

[0010]

[0008] A rotating electric machine control device according to the present disclosure controls a rotating electric machine having m-phase armature windings of a first set (m is an integer greater than or equal to 3) and m-phase armature windings of a second set, via an inverter of a first set and an inverter of a second set, respectively, the rotating electric machine control device executes alternator generation control that operates the inverter of each set as a rectifier by an induced voltage generated in the armature windings of each set by rotation of the rotating electric machine, and operates the rotating electric machine as a generator; and calculates estimation values ​​of applied voltages that are applied to the armature windings of each set, on the basis of detection values ​​of current flowing in the armature windings of each set when the alternator generation control is executed, wherein a minimum value of phase angle differences greater than 0 between a plurality of phase angles obtained by collecting a phase angle and a reverse phase angle of the armature winding of each phase in each set is set as the minimum phase angle difference among phases of each set, and a phase angle difference of an electrical angle between the m-phase armature windings of the first set and the m-phase armature windings of the second set is equal to 1 / 2 of the minimum phase angle difference among the phases of each set.

[0011]

[0009] According to the rotating electric machine control device of the present disclosure, estimation values ​​of applied voltages that are commonly applied to the armature windings of each set can be calculated on the basis of detection values ​​of current flowing in the armature windings of each set when the alternator generation control is executed. At this time, a phase angle difference of the electrical angle between the m-phase armature windings of the first set and the m-phase armature windings of the second set is set to be 1 / 2 of the minimum phase angle difference among the phases of each set. Therefore, the current detection value of the specific phase and the current detection value of a phase whose phase angle difference becomes ir / 2 can be obtained.Therefore, by using the phase angle difference between the current detection values ​​of each set and each phase, the fundamental wave and the harmonic wave of the first-order component of electric angle included in the current detection value can be separated and detected, and the estimation values ​​of applied voltages can be calculated with good accuracy. Brief description of the drawings

[0012]

[0010] [Fig.l] is a configuration diagram of the rotating electric machine and the rotating electric machine control device according to embodiment 1; [Fig.2] is a figure explaining the phase angle difference between the armature windings of the first set and the armature windings of the second set according to embodiment 1; [Fig.3] is a block diagram of the rotating electric machine control device according to embodiment 1; [Fig.4] is a hardware configuration diagram of the rotating electric machine control device according to embodiment 1; [Fig.5] is a chronological diagram explaining the behavior of the armature winding currents when the alternator generation control is executed, according to embodiment 1; [Fig.6] is a figure explaining the first-order component of electric angle of the current vector, according to embodiment 1; [Fig.7] is a figure explaining the fifth-order component of electric angle of the current vector, according to embodiment 1; [Fig.8] is a figure explaining the first-order component of electric angle of the current vector, according to embodiment 1; [Fig.9] is a figure explaining the fifth-order component of electric angle of the current vector, according to embodiment 1; [Fig. 10] is a chronological diagram explaining the behavior of the current and the activation / deactivation of the switching devices, according to embodiment 1; [Fig.l 1] is a time diagram explaining the change of the on / off timing of the switching devices by the change of the phase angle difference between the first-order component of electrical angle and the fifth-order component of electrical angle, according to embodiment 1; [Fig. 12] is a figure explaining the phase angle difference between the current vector and the voltage vector according to embodiment 1; [Fig. 13] is a figure explaining the relationship between the relative phase angle and the amplitude ratio between the first-order component of electric angle and the fifth-order component of electric angle, and the amount of phase angle displacement, according to embodiment 1; [Fig. 14] is a figure explaining the simplified relationship between the amplitude ratio between the first-order component of electric angle and the fifth-order component of electric angle, and the amount of phase angle shift, according to embodiment 1; [Fig. 15] is a time-series diagram explaining the behavior of the bus current, if the current comprises only the first-order electrical angle component, according to embodiment 1; [Fig. 16] is a time-series diagram explaining the behavior of the bus current, if the current includes the first-order electrical angle component and the fifth-order electrical angle component, according to embodiment 1; [Fig. 17] is a diagram of the rotating electric machine serving as a generator motor for the vehicle, according to claim 1; [Fig. 18] is a figure explaining the phase angle difference between the armature windings of the first set and the armature windings of the second set according to embodiment 2; [Fig. 19] is a figure explaining the first-order component of electric angle of the current vector, according to embodiment 2; [Fig.20] is a figure explaining a third-order component of electric angle of the current vector, according to embodiment 2; [Fig.21] is a figure explaining the first-order component of electric angle of the current vector, according to embodiment 2; and [Fig.22] is a figure explaining the third-order component of electric angle of the current vector, according to embodiment 2. DETAILED DESCRIPTION OF THE EMBODIMENTS

[0013]

[0011] 1. Embodiment 1 A rotating electric machine control device 30 (hereinafter referred to simply as the control device 30) according to embodiment 1 will be explained hereinafter with reference to the drawings. [Fig.l] is a configuration diagram of a rotating electric machine 1, a first set inverter 5a, a second set inverter 5b, a converter 9, and the control device 30, according to the present embodiment.

[0014]

[0012] 1-1. Rotating electric machine 1 The rotating electric machine 1 is provided with a stator 18 and a rotor 14 disposed on the radial direction inner side of the stator 18. First set m-phase armature windings and second set m-phase armature windings are wound around an iron core of the stator 18. Although m can be set to an integer greater than or equal to 3, m is set to 3 in the present embodiment. The stator 18 is provided with first set three-phase armature windings Cul, Cvl, Cwl of Ul phase, VI phase and W1 phase and second set three-phase armature windings Cu2, Cv2, Cw2 of U2 phase, V2 phase and W2 phase. The three-phase armature windings of each set can be connected by a star connection, or can be connected by a delta connection. A field winding 4 is wound around the iron core of the rotor 14, and an electromagnet is provided.A permanent magnet may be provided in the rotor 8 with the field winding 4.

[0015]

[0013] In the present embodiment, as shown in the diagram of [Fig.2], a phase angle difference X of the electrical angle of the phase angles of the three-phase armature windings of the second set Cu2, Cv2, Cw2 with respect to phase angles of the three-phase armature windings of the first set Cul, Cvl, Cwl is set to ir / 6 (30 degrees). The electrical angle becomes an angle obtained by multiplying the number of pole pairs of the magnet by the mechanical angle of the rotor 14.

[0016]

[0014] Electrical constants, such as an inductance value and a resistance value of the three-phase armature windings of each set, are defined not to be different between the two sets.

[0017]

[0015] A rotation sensor 15 that detects the electrical angle (the magnetic pole position) of the rotor 14 is provided in the rotor 14. An output signal of the rotation sensor 15 is input to the controller 30. Various types of sensors, such as a Hall element, a resolver, or an encoder, are used for the rotation sensor 15. The rotation sensor 15 may not be provided, and the electrical angle (the magnetic pole position) may be estimated based on current information that is obtained by superimposing a harmonic wave component on the current command value, as described below (a so-called sensorless system).

[0018]

[0016] 1-2. DC power source 2 The DC power source 2 delivers a DC voltage Vdc to the inverter of the first set 5a, to the inverter of the second set 5b and to the converter 9. Any device that delivers a DC voltage, such as a battery, a DC-DC converter, a diode rectifier and a PWM rectifier, can serve as the DC power source 2. A smoothing capacitor 3 is connected in parallel to the DC power source 2.

[0019]

[0017] 1-3. Inverter The inverter of the first set 5a performs power conversion between the DC power source 2 and the three-phase armature windings of the first set. The inverter of the second set 5b performs power conversion between the DC power source 2 and the three-phase armature windings of the second set.

[0020]

[0018] The inverter of the first set 5a is provided with three series circuits in each of which a high potential side switching device SP1 connected to the side high potential of DC power source 2 and a low potential side switching device SN1 connected to the low potential side of DC power source 2 are connected in series, corresponding to respective phases of the three-phase armature windings of the first set. A connecting node of two switching devices in each series circuit is connected to the armature winding of the corresponding phase of the first set.

[0021]

[0019] The inverter of the second set 5b is provided with three series circuits in each of which a high potential side switching device SP2 connected to the high potential side of the DC power source 2 and a low potential side switching device SN2 connected to the low potential side of the DC power source 2 are connected in series, corresponding to respective phases of the three-phase armature windings of the second set. A connecting node of two switching devices in each series circuit is connected to the armature winding of the corresponding phase of the second set.

[0022]

[0020] Each inverter switching device of each set has a function of a diode connected in reverse parallel. For example, an IGBT (insulated gate bipolar transistor) in which a diode is connected in reverse parallel, a bipolar transistor in which a diode is connected in reverse parallel, a MOSFET (metal oxide semiconductor field effect transistor) having a parasitic diode function connected in reverse parallel, or the like is used for the inverter switching device of each set. A gate terminal of each switching device is connected to the control device 30 via a gate drive circuit and the like. Each switching device is turned on or off by the switching signal output from the control device 30.

[0023]

[0021] The first set armature current sensor 8a is a current detection circuit that detects a current flowing in the armature winding Cul, Cvl, Cwl of each phase of the first set. The second set armature current sensor 8b is a current detection circuit that detects a current flowing in the armature winding Cu2, Cv2, Cw2 of each phase of the second set. In the present embodiment, the induced air current sensor 8a, 8b of each set is provided on the electric wire that connects the series circuit of the switching device of each phase and the armature winding of each phase. The output signal of the induced air current sensor 8a, 8b of each phase of each set is input to the control device 30. The induced air current sensor is a current sensor, such as a Hall element, or a shunt resistor. The induced air current sensor of each phase can be connected in series to the series circuit of the switching devices of each phase.

[0024]

[0022] 1-4. Converter 9 The converter 9 is provided with switching devices and performs power conversion between the DC power source 2 and the field winding 4. In the present embodiment, the converter 9 is an H-bridge circuit which is provided with two series circuits in each of which a high-potential side switching device SP connected to the high-potential side of the DC power source 2 and a low-potential side switching device SN connected to the low-potential side of the DC power source 2 are connected in series. The connection node of the high-potential side switching device SP1 and the low-potential side switching device SN1 in the first series circuit 28 is connected to one end of the field winding 4.The connecting node of the high potential side switching device SP2 and the low potential side switching device SN2 in the second series circuit 29 is connected to the other end of the field winding 4. .

[0025]

[0023] The IGBT in which the diode is connected in reverse parallel, the bipolar transistor in which the diode is connected in reverse parallel, the MOSFET or the like is used for the switching device of the converter 9. A gate terminal of each switching device is connected to the control device 30 via a gate drive circuit and the like. Each switching device is turned on or off by the switching signal output from the control device 30.

[0026]

[0024] The converter 9 may have other configurations. For example, the low-side switching device SN 1 of the first series circuit 28 may be replaced by a diode, and the high-side switching device SP2 of the second series circuit 29 may be replaced by a diode.

[0027]

[0025] A field current sensor 6 is a current detection circuit that detects a field current that is a current flowing through the field winding 4. In the present embodiment, the field current sensor 6 is provided on the electric wire that connects the field winding 4 and the converter 9. The field current sensor 6 may be provided in other parts that can detect the field current. The output signal of the field current sensor 6 is input to the device control 30. The field current sensor 6 is a current sensor, such as a Hall element, or a shunt resistor.

[0028]

[0026] 1-5. Control device 30 The control device 30 controls the rotating electric machine 1 via the first set inverter 5a, the second set inverter 5b, and the converter 9. As shown in [Fig. 3], the control device 30 is provided with functional units, such as a rotation detection unit 31, an armature current detection unit 32, a control commutation determination unit 33, an alternator generation control unit 34, an estimation unit 35, an inverter control unit 36, a field current detection unit 37, and a field current control unit 38. Each function of the control device 30 is performed by processing circuits provided in the control device 30. Specifically, as shown in [Fig.4], the control device 30 is provided, as processing circuits, with an arithmetic processor (computer) 90 as a CPU (central processing unit), storage devices 91 which exchange data with the arithmetic processor 90, an input circuit 92 which inputs external signals into the arithmetic processor 90, an output circuit 93 which outputs signals from the arithmetic processor 90 to the outside, a communication circuit 94 which performs data communication with external devices, and the like.

[0029]

[0027] . As the arithmetic processor 90, there may be provided an ASIC (application-specific integrated circuit), an IC (integrated circuit), a DSP (digital signal processor), an FPGA (field programmable gate array), various types of logic circuits, various types of signal processing circuits, and the like. As the arithmetic processor 90, there may be provided a plurality of elements of the same type or elements of different types, and each processing may be shared and executed. As storage apparatuses 91, there are provided a RAM (random access memory) that can read data from and write data from the arithmetic processor 90, a ROM (read only memory) that can read data from the arithmetic processor 90, and the like.The input circuit 92 is connected to various types of sensors and switches such as the rotation sensor 15, the armature current sensor 8a, 8b of each set, and the field current sensor 6, and is provided with an analog-to-digital converter and the like for inputting output signals from the sensors and switches into the arithmetic processor 90. The output circuit 93 is connected to electrical loads such as a gate drive circuit which turns the devices on and off. switching of the inverters INI, IN2 of the first set and the second set, and the converter 9, and is provided with a drive circuit and similar elements for delivering a control signal from the arithmetic processor 90. The communication circuit 94 communicates with the external device.

[0030]

[0028] The arithmetic processor 90 then executes software elements (programs) stored in the storage apparatus 91, such as a ROM, and cooperates with other hardware devices in the control device 30, such as the storage apparatus 91, the input circuit 92, and the output circuit 93, so that the respective functions of the control units 31 to 38 provided in the control device 30 are realized. Various types of parameter data items to be used in the control units 31 to 38 are stored, as software elements (programs), in the storage apparatus 91, such as a ROM. Each function of the control device 30 will be described in detail below.

[0031]

[0029] The rotation detection unit 31 detects a magnetic pole position 0 (an electrical angle 0 of the rotor) and an electrical angle speed co of the rotor within the electrical angle. In the present embodiment, the rotation detection unit 31 detects the magnetic pole position 0 (the electrical angle 0) and the electrical angle speed co within the electrical angle, based on the output signal of the rotation sensor 15. The magnetic pole position is defined in the direction of the N pole of the electromagnet provided in the rotor. In the present embodiment, the magnetic pole position 0 (the electrical angle 0) is a position (electrical angle) of the magnetic pole (N pole) within the electrical angle based on the phase angle of the phase armature winding U1 of the first set.Depending on the phase angle difference ir / 6 between the armature windings of the first set and the armature windings of the second set as shown in [Fig.2], the position (electric angle) of the magnetic pole (N pole) in the electrical angle based on the phase angle of the armature winding of phase U2 of the second set becomes O-ir / 6.

[0032]

[0030] The rotation detection unit 31 can estimate the electrical angle (the magnetic pole position) without using the rotation sensor, on the basis of current information which is obtained by superimposing a harmonic wave component on the current instruction value (i.e., a sensorless system).

[0033]

[0031] The armature current detection unit 32 detects the current detection values ​​iul, ivl, iwl flowing in the three-phase armature windings of the first set, based on the output signal of the first set armature current sensor 8a. The armature current detection unit 32 detects the current detection values ​​iu2, iv2, iw2 flowing in the three-phase armature windings of the second set, based on the output signal of the second set armature current sensor 8b. For each set, the armature current sensor can detect the current detection values ​​of two phases, and the current detection value of the remaining phase can be calculated based on the value

[0034] of detecting the current detection values ​​of the two phases.

[0032] The field current detection unit 37 detects the field current if it flows through the field winding 4, based on the output signal of the current sensor

[0035] of field 6.

[0033] The field current control unit 38 controls the activation / deactivation of the switching devices of the converter 9, and applies a voltage to

[0036] field winding 4.

[0034] The field current control unit 38 calculates a field current command value If*, based on the electrical angle speed co and the output command value, in each of the alternator generation control and the inverter control. In addition to the electrical angle speed co and the value output instruction, the DC voltage Vdc can also be taken into account.

[0037]

[0035] The field current control unit 38 performs feedback control that changes the field voltage instruction value Vf so that the field current detection value if approaches the field current instruction value If*. The field current control unit 38 controls the switching devices of the converter 9 to be turned on / off by PWM control,

[0038] based on the field voltage instruction value Vf.

[0036] 1-5-1. Control switching determination unit 33 The control switching determination unit 33 determines whether or not to execute the inverter control or the alternator generation control, on the basis of the electric angle speed co and the output instruction value. For example, the control switching determination unit 33 determines to execute the inverter control when the electric angle speed co and the output instruction value are within a preliminarily set execution region of the inverter control; and determines to execute the alternator generation command when the electrical angle speed co and the output instruction value are within a preliminarily defined execution region of the alternator generation command. In addition to the electrical angle speed co and the output instruction value, the DC voltage Vdc can also be taken into account.

[0039]

[0037] As the output command value, an output torque command value, an output current command value, or an output power command value may be used depending on the system in which the rotating electric machine 1 is used. The output command value may be calculated inside the controller 30, and it may be transmitted from the external controller.

[0040]

[0038] 1-5-2. Alternator generation control unit 34 When the control switching determination unit 33 determines to execute the alternator generation control, the alternator generation control unit 34 executes the alternator generation control which operates the inverters 5a, 5b of each set as a rectifier by an induced voltage generated in the armature windings of each set by the rotation of the rotating electric machine 1, and operates the rotating electric machine 1 as a generator.

[0041]

[0039] For each set, when the induced voltage of the armature windings of each phase generated by rotation exceeds the high potential of the DC power source 2 or is lower than the low potential of the DC power source 2, the diode of the high-potential side switching device or the low-potential side switching device of the corresponding phase is energized, and the inverter operates as a full-wave rectifier circuit. When performing such diode rectification, the alternator generation control unit 34 turns off all the inverter switching devices of each set constantly.

[0042]

[0040] Furthermore, synchronous rectification can be realized. This means that the alternator generation control unit 34 activates the switching device provided in parallel with the diode, when a current flows through the diode by the induced voltage. Therefore, since a current flows through the switching device instead of the diode, the power loss can be reduced and the amount of heating can be reduced. For example, for each set, the alternator generation control unit 34 determines the diode of the switching device switching the high potential side or the low potential side switching device of each phase through which a current flows, based on the current detection value of each phase; and turns on the switching device corresponding to the diode through which the current flows, and turns off the switching device corresponding to the diode through which the current does not flow.

[0043]

[0041] For example, synchronous rectification is performed in the region where the phase current amplitude is large, and diode rectification is performed in the region where the phase current amplitude is small in order to prevent erroneous determination.

[0044]

[0042] When the alternator generation command is executed, the DC voltage Vdc applied to the armature windings of each phase becomes 1 pulse which is turned on or off every 180 degrees.

[0045]

[0043] 1-5-3. Estimation unit 35 The estimation unit 35 calculates estimation values ​​of applied voltages that are currently applied to the armature windings of each set, based on the detection values ​​of current flowing in the armature windings of each set when the alternator generation control is executed.

[0046]

[0044] A minimum value of phase angle differences greater than 0 between a plurality of phase angles obtained by collecting a phase angle and a reverse phase angle of the armature winding of each phase in each set is defined as a minimum phase angle difference AOmin among phases of each set. A phase angle difference of the electrical angle between the three-phase armature windings of the first set and the three-phase armature windings of the second set is defined as 1 / 2 of the minimum phase angle difference AOmin among the phases of each set. In the present embodiment, as shown in [Fig.2], in the first set, the plurality of phase angles obtained by collecting the phase angle and reverse phase angle of the armature winding of each phase become the direction and opposite direction of the arrow representing the phase angle and reverse phase angle of phase Ul, the direction and opposite direction of the arrow representing the phase angle and reverse phase angle of phase VI, and the direction and opposite direction of the arrow representing the phase angle and reverse phase angle of phase Wl. The minimum phase angle difference AOmin which is the minimum value of the phase angle differences greater than 0 between the plurality of phase angles becomes ir / 3. In .

[0047] the second set, the plurality of phase angles obtained by collecting the phase angle and reverse phase angle of the armature winding of each phase become the direction and opposite direction of the arrow representing the phase angle and reverse phase angle of phase U2, the direction and opposite direction of the arrow representing the phase angle and reverse phase angle of phase V2, and the direction and opposite direction of the arrow representing the phase angle and reverse phase angle of phase W2. The minimum phase angle difference AOmin which is the minimum value of the phase angle differences greater than 0 between the plurality of phase angles becomes ir / 3.The phase angle difference X of the electrical angle between the three-phase armature windings of the first set and the three-phase armature windings of the second set is defined as ir / 6 which is 1 / 2 of the minimum phase angle difference AOmin (=ir / 3) among the phases of each set.

[0045] <Explication de principe de l’estimation de tension et de la définition d’angle de phase> [Fig.5] shows the current waveform of each phase of each set when the alternator generation control is executed. In the alternator generation control, the DC voltage Vdc applied to the armature winding of each phase becomes 1 pulse which is turned on or off every 180 degrees, and becomes similar to the state in which 1 pulse control is performed. Therefore, the current of each phase of each set becomes a waveform in which a harmonic wave of the fifth-order component of electrical angle is superimposed on a fundamental wave of a first-order component of electrical angle. The current of each phase of each set is given by equation (1). [Math. 1] <h2 style=";text-align:left;direction:ltr">= Ir sin Ir sin(ût + 5t) + 1^ sin(5cot + 52) / 2 \ / n>t + — -ît 1 + / 5 sin 1 5éot + 82 2 \ + 3^ iwi = h sin / 2 \ / \a)t + ^ + - TT 1 + Z5 sin 1 5cot + 82 2 A 3 J < iu2 = h sin | n>t + — — ) + Z5 sin 5tot + ô2 — < 6 / \ 5 A 6 / iv2 = Zi sin | ' 5 \ 7 ait + — -n + Z5 sin ( + 82 < 6 / v 7T\ 6 / = h sin ( 7T\ . / eût + + —J + / 5 sin + 82 + 7T\ 2 / <h2 style=";text-align:left;direction:ltr"> <h2 style=";text-align:left;direction:ltr">

[0048]

[0046] <h2 style=";text-align:left;direction:ltr"> Herein, Il is a current magnitude of the first-order electrical angle component, 15 is a current magnitude of the fifth-order electrical angle component, ôl is a phase angle relative to a current phase angle eut of the first-order electrical angle component, ô2 is a phase angle relative to a current phase angle 5cot of the fifth-order electrical angle component. For expression by the vector diagram, the first-order electrical angle component of the current of each phase of each set has a phase angle relationship which is shown in [Fig.6], and the fifth-order electrical angle component of the current of each phase of each set has a phase angle relationship which is shown in [Fig.7].

[0049]

[0047] iu2-iv2 is deduced as in equation (2) from equation (1). Herein, 2cos(ir / 6) =V3. [Math. 2] 7T i u2 — ^2 — h sin((Dt + 5 X ) 2 cos — 6 n — / 5 sin(5o)t + 52) 2 cos — • • • (2) 6

[0050]

[0048] When deforming using equation (2) and the first equation of equation (1), the first-order electrical angle component iul_l and the fifth-order electrical angle component iul_5 of the phase iul current U1 of the first set can be expressed by the following equation. [Math. 3] r 1 iui_i = ;i sin(tot + ^)=- 1 ^i_5 = ^5 sm(5tot + 52) = - 1. ^-u2 2VU1 Vf” J l-u2 ^v2 ~ tT 2 COS7-0 J

[0051]

[0049] As shown in equation (2) and [Fig.6], the first-order component of electric angle of iu2-iv2 becomes ^3 times the first-order component of electric angle of iul. As shown in Equation (2) and [Fig.7], the fifth-order component of electric angle of iu2-iv2 becomes -V3 times the fifth-order component of electric angle of iul. Therefore, as shown in the first equation of Equation (3), by adding (iu2-iv2) / ^3 to iul, and dividing by 2, the fifth-order component of electric angle of iul can be canceled, and the first-order component of electric angle of iul can be extracted. As shown in the second equation of Equation (3), by subtracting (iu2-iv2) / 'V3 from iul, and dividing by 2, the first-order component of electric angle of iul can be canceled, and the fifth-order component of electric angle of iul can be extracted.

[0052]

[0050] iwl-ivl is deduced as in equation (4) from equation (1). Herein, 2cos(ir / 6) =V3. [Math. 4] / n\ n W — hi — h sin ( (^t + 5 r + — ) 2 cos — V 2 / 6 / n\ n — / 5 sin (5ri>t + Ô2 + — ) 2 cos — ---(4) v 2 / 6

[0053]

[0051] When deforming using equation (4) and the sixth equation of equation (1), the first-order component of electric angle iw2_l and the fifth-order component of electric angle iw2_5 of current value iw2 of phase W2 of the second set can be expressed by the following equation. [Math. 5] r / TT iw2_i = sin (mt + + - jW2_5 = h sin (5mt + ^+^

[0054]

[0052] As represented in Equation (4) and [Fig.8], the first-order electric angle component of iwl-ivl becomes ^3 times the first-order electric angle component of iw2. As represented in Equation (4) and [Fig.9], the fifth-order electric angle component of iwl-ivl becomes -V3 times the fifth-order electric angle component of iw2. Therefore, as represented in the first equation of Equation (5), by adding (iwl-ivl) / ^3 to iw2, and dividing by 2, the fifth-order component of electric angle of iw2 can be canceled, and the first-order component of electric angle of iw2 can be extracted. As shown in the second equation of equation (5), by subtracting (iwl-iv 1) / ^3 from iw2, and dividing by 2, the first-order component of electric angle of iw2 can be canceled, and the fifth-order component of electric angle of iw2 can be extracted.

[0055]

[0053] Herein, the phase angle of iw2 in equation (5) advances by ir / 2 relative to the phase angle of iul. As shown in equation (6), when the sine in equation (5) is converted to cosine, equation (5) becomes the cosine version of iul. [Math. 6] = cos(6it + = 1$ cos(5eot + 52)

[0056]

[0054] Therefore, as shown in Equation (7), based on the first-order electrical angle component of iul in the first equation of Equation (3), and the first-order electrical angle component of iw2 in Equation (5) and the first equation of Equation (6), the amplitude II and the phase angle A01 of the first-order electrical angle component of iul can be calculated. [Math. 7] ) = had + S1 = tan 1 I ± sin(n)t + cos(d)t + ^u2 ^v2 \ V3 j ^wl j V3 /

[0057]

[0058]

[0059]

[0055] As shown in Equation (8), based on the fifth-order electrical angle component of iul in the second equation of Equation (3), and the fifth-order electrical angle component of iw2 in Equation (5) and the second equation of Equation (6), the amplitude 15 and phase angle A05 of the fifth-order electrical angle component of iul can be calculated. [Math. 8] / 5 = i -j \2 / ÿ -i \2 77 Hul I ' I ^w2 ~ I ' A05 = So)t + ô2 = tan 1 1 -----—-----—■ b Y4 cos(5eot + Ô2) (: _ ^u2 ^v2 \ U1 V3 ] j ^wl I ^w2 r; /

[0056] From the second equation of equation (7) and the second equation of equation (8), a relative phase angle A05-5A01 of the fifth-order component of electric angle with respect to the phase angle A01 of the first-order component of electric angle is given by equation (9). [Math. 9] Û05 - 5â0! = S2 - 5¾ V3 (: I ^u2 ; 1 ^W1 lv2 V3 ...(9)

[0057] Equation (10) is obtained by squaring each of the first equation and the second equation of equation (3). Therefore, by performing low-pass filter processing on each of the first equation and the second equation of equation (10), a square of the amplitude II of the first-order component of electric angle and a square of the amplitude 15 of the fifth-order component of electric angle electric can be calculated. Without using equation (5) of iw2 whose phase angle is ahead by ir / 2 with respect to the phase angle of iul as in equation (7) and equation (8), the amplitude II of the first-order component of electric angle and the amplitude 15 of the fifth-order component of electric angle can be calculated only by equation (3) of iul. [Math. 10] < ■ ■ 2 2i„ii 2 = laughed 2 [1 - cos{2(ù>t + O] = 2 Yes + L ) 2t u is 2 = CU - cos{2(5a>t + 52)}] = ~ ~ ■••(10)

[0060]

[0058] <Généralisation du résultat de déduction> In the above, when m=3, the equations have been deduced for iul of phase U1 and iw2 of phase W2 whose phase angle difference with respect to phase U1 is jt / 2. This deduction result will be generalized.

[0061]

[0059] Assuming that the phase angle difference between the armature windings of the first set and the armature windings of the second set is X, as shown in equation (11), phase angle lag amounts of phase U2, phase V2, and phase W2 of the second set relative to phase U1 become X, X+2 / 3ir, and X-2 / 3ir, respectively. If the phase angle difference of any of the U2 phase, the V2 phase and the W2 phase of the second set with respect to the U1 phase becomes +ir / 2 or -ji / 2, as mentioned above, the magnitude and phase angle of the first-order component of electrical angle, and the magnitude and phase angle of the fifth-order component of electrical angle can be calculated on the basis of iul of the U1 phase, and the current value of a phase of the second set whose phase angle difference with respect to the U1 phase angle is +ir / 2 or -ji / 2.The phase angle difference X must fall within a range represented in equation (12), in order to maintain equation (11) which defines the relationship of phase U2, phase V2 and phase W2 of the second set with respect to phase Ul. The phase angle difference X which satisfies equation (11) and equation (12) becomes jt / 6, as represented in equation (13). [Math. 11] [Math. 12] 0 <X<|---(12) [Math. 13] n X = ----(13) o

[0062]

[0060] The minimum phase angle difference AOmin among phases of each set which is a minimum value of phase angle differences greater than 0 between a plurality of phase angles obtained by collecting a phase angle and an inverse phase angle of the armature winding of each phase in each set is ir / 3. The phase angle difference X of the electrical angle between the three-phase armature windings of the first set and the three-phase armature windings of the second set becomes ir / 6 which is 1 / 2 of the minimum phase angle difference AOmin (=ir / 3) among the phases of each set.

[0063]

[0061] Generalizing this deduction result, when M is an odd number, the minimum phase angle difference AOmin among phases of each set which is a minimum value of phase angle differences greater than 0 between a plurality of phase angles obtained by collecting a phase angle and an inverse phase angle of the armature winding of each phase in each set is ir / m. The phase angle difference X of the electrical angle between the m-phase armature windings of the first set and the m-phase armature windings of the second set becomes 1 / 2 of the minimum phase angle difference AOmin among the phases of each set, i.e., ir / m / 2.

[0064]

[0062] In the above equation (3), to calculate the first-order electrical angle component and the fifth-order electrical angle component of the current value iul of phase Ul, the current value iul of phase U1, and the current value iu2 of phase U2 of which a phase angle difference with respect to phase Ul is jt / 6 (=ir / m / 2), and the current value iv2 of phase V2 whose phase angle difference from phase U1 is 5ir / 6 (=jr-jr / m / 2) are used. In equation (5) above, to calculate the first-order electrical angle component and the fifth-order electrical angle component of the current value iw2 of phase W2 whose phase angle difference from phase U1 is ji / 2, the current value iw2 of phase W2, the current value iwl of phase W1 whose phase angle difference from phase W2 is ir / 6 (=ir / m / 2), and the current value ivl of phase V1 whose phase angle difference from phase W2 is 5ir / 6 (=jr-jr / m / 2) are used.

[0065]

[0063] For generalization purposes, phase U1 is replaced by phase Al which is any phase among the m phases of the first set. Then, equation (3) can be generalized by equation (14) which calculates a first-order component of electric angle ial_l and a (2m-l)-th order component of electric angle ial_2m-l of the current value ial of phase Al. [Math. 14] COS ~— [2m iai_2m-i = hm-1 sin{(2m - l>t + 52) = “ lb2 lc2 COS I q— I \2mJ ■ • • (14) Herein, ib2 is a current value flowing through the armature winding of phase B2, among the m phases of the second set, a phase angle difference of which with respect to phase A1 is (jr-jr / m / 2). ic2 is a current value flowing through the armature winding of phase C2, among the m phases of the second set, a phase angle difference of which with respect to phase A1 is (jr-jr / m / 2).

[0066]

[0064] Equation (5) and equation (6) can be generalized by equation (15) which calculates the first-order component of electric angle ia2_l and the (2m-l)-th order component of electric angle ia2_2m-l of the current value ia2 of phase A2, among the m phases of the second set, whose phase angle difference with respect to phase Al is ji / 2. [Math. 15] ( x ^a2 i a21= h sin lcüt + Ô1+ — ] = Ii cosÇûJt + ^) = — + here fn \ COS T— \2mJ ^a2_2m —1 hm-1 t zy Q lh 1 c 1 = 12m-i cos{(2m - l>t + 52} = —--- 2 COS(5— \2m>

[0067]

[0065] Herein, ibl is a current value flowing through the armature winding of phase Bl, among the m phases of the first set, a phase angle difference of which with respect to phase A2 is ir / m / 2. here is a current value flowing through the armature winding of phase Cl, among the m phases of the first set, a phase angle difference of which with respect to phase A2 is (jt-jt / m / 2).

[0068]

[0066] Equation (7) can be generalized by Equation (16) using Equation (14) and Equation (15). Therefore, the estimation unit 35 calculates the amplitude II and the phase angle A01 of the first-order component of electrical angle, using Equation (16), on the basis of the current detection value ial of phase A1, the current detection value ib2 of phase B2, the current detection value ic2 of phase C2, the current detection value ia2 of phase A2, the current detection value ibl of phase B1, and the current detection value ici of phase C1. [Math. 16]

[0069]

[0067] Equation (8) can be generalized by equation (17) using equation (14) and equation (15). Therefore, the estimation unit 35 calculates an amplitude I2m-1 and a phase angle 02m-1 of the (2m-l)-th order electrical angle component, using equation (17), based on the current detection value ial of phase Al, the current detection value ib2 of phase B2, the current detection value ic2 of phase C2, the current detection value ia2 of phase A2, the current detection value ibl of phase B1 and the current detection value ici of phase Cl. [Math. 17] r 1 li = - 2 A < A02m-i = (2m — l)cot + ô2 = tan-1

[0070]

[0068] Equation (9) can be generalized by Equation (18) using the second equation of Equation (16) and the second equation of Equation (17). Therefore, the estimation unit 35 calculates a relative phase angle of the (2m-l)-th order component of electrical angle based on the phase angle A01 of the first order component of electrical angle, using Equation (18), based on the current detection value ial of phase A1, the current detection value ib2 of phase B2, the current detection value ic2 of phase C2, the current detection value ia2 of phase A2, the current detection value ibl of phase B1, and the current detection value ici of phase C1. [Math. 18] A02m-i - (2m / Cl - 1)M, = S2 - (2m - 1)¾ C2 C2 \ lb2 lc2 \ / Ci, 2 ( n \ 2 + / n \ = tan-1 ----- COS ô— — (2m — 1) tan-1 ----- COS ® ---(18) ^a2 ibi - Ci C2 , Ci Cl , 2 / n \ , 2 + (TT \ \ cos Gm) / \ cos \.2m) /

[0071]

[0069] Equation (10) can be generalized to equation (19) using equation (14). Therefore, the estimation unit 35 calculates the first-order electrical angle component ial_l of the current detection value ial of phase Al, using the first equation of equation (14), on the basis of the current detection value ial of phase Al, current detection value ib2 of phase B2 and current detection value ic2 of phase C2; ​​and calculates the amplitude II of the first-order component of electrical angle, based on a value obtained by passing a square value of the first-order component of electrical angle ial_l through a low-pass filter. Herein, the estimation unit 35 calculates a square root of a value obtained by multiplying 2 by the square value of ial_l after the low-pass filter, as the amplitude II of the first-order component of electrical angle.The estimation unit 35 calculates the (2m-l)-th order electrical angle component ial_2m-l of the current detection value ial of phase Al, using the first equation of equation (14), on the basis of the current detection value ial of phase Al, the current detection value ib2 of phase B2 and the current detection value ic2 of phase C2; ​​and calculates the amplitude I2m-1 of the (2m-l)-th order electrical angle component, on the basis of a value obtained by passing a square value of the (2m-l)-th order electrical angle component l_2m-l through a low-pass filter. Herein, the estimation unit 35 calculates a square root of a value obtained by multiplying 2 by the square value of ial_2m-l after the low-pass filter, as the amplitude I2m-1 of the (2m-l)-th order component of electrical angle. [Math. 19] 2iai 12 = Utl - cos{2(&)t + O] = dy + ^2 , 2\ 2 H 1 '2i al 2m -i 2 = / 2m-i 2 [l - cos{2((2m - + 52)}] • • • (19)

[0072]

[0070] A cutoff frequency of the low-pass filter on the calculation value of the first equation of equation (19) is made lower than twice the electrical angle velocity co (electrical angle frequency). A cutoff frequency of the low-pass filter on the calculation value of the second equation of equation (19) is made lower than 2x(2m-l) times the electrical angle velocity co (electrical angle frequency). A first-order delay filter or moving average processing is used as the low-pass filter.

[0073]

[0071] cCalculation of applied voltage estimation values> The calculation of the applied voltage estimation values ​​when the alternator generation command is executed will be explained below.

[0074]

[0072] When the current iul of phase U1 at the time of generating alternator power is given by equation (20), the waveform of current iul for one electrical angle cycle is as shown in the upper graph of [Fig. 10]. At this time, the switching on / off (or diode energization or de-energization) of the high potential side switching device SPul and the low potential side switching device SNul of phase U1 is as shown in the middle graph and the lower graph of [Fig. 10]. When the high potential side switching device SPul is switched on, the DC voltage Vdc is applied to the armature winding of phase U1 and, when the low potential side switching device SNul is switched on, 0V is applied to the armature winding of phase Ul. In [Fig.10], it is assumed that synchronous rectification with good accuracy in the on / off timing of switching devices is realized, or that diode rectification is realized. [Math. 20] i ul = sin ai + 0.1 sin(5a)t + tt) • • • (20)

[0075]

[0073] [Fig. 11] shows the on / off waveform of the high-potential side switching device SPul when the phase current iul Ul at the time of generator power generation is given by Equation (20), Equation (21), or Equation (22). As described above, the on / off waveform of the switching device corresponds to the waveform of the applied voltage. The solid line is the waveform of Equation (20), the broken line is the waveform of Equation (21), and the dotted line is the waveform of Equation (22). [Math. 21] / 5 \ i ul = sinéot + 0.1 sin 5cot + -n] ---(21) \ 6 / [Math. 22] / 2 \ i ul = sinDt + 0.1 sin I 5 <Dt +-7T I ---(22) \ /

[0076]

[0074] If only the first-order component of electric angle (the wave fundamental) is contained, the phase angle of the applied voltage can advance by ir with respect to the phase angle of the current. However, the fifth-order electrical angle component is superimposed on the first-order electrical angle component. The phase angle at which the positive or negative of the current is switched is different from the phase angle at which the positive or negative of the first-order electrical angle component is switched. This means that, depending on the phase angle difference and the magnitude ratio between the first-order electrical angle component and the fifth-order electrical angle component, the phase angle of the applied voltage with respect to the phase angle of the current changes.

[0077]

[0075] Therefore, as shown in Equation (23) and [Fig. 12], the phase angle 0v of the applied voltage vector in the d-axis and q-axis rotation coordinate system must be delayed by (jt-a) relative to the phase angle 0i of the current vector in the d-axis and q-axis rotation coordinate system. Herein, a is a phase angle displacement amount. The method for calculating the phase angle displacement amount a is described below. Herein, the phase angle 0i of the current vector is a phase angle of the current vector of the d-axis and q-axis currents of the first set, and a phase angle of the current vector of the d-axis and q-axis currents of the second set. The phase angle 0i of the current vector of the first set and the phase angle 0i of the current vector of the second set generally become equal. [Math. 23] 9 v = 0i-(jt-a) • • • (23)

[0078]

[0076] The d-axis is defined in the direction of the N pole (magnetic pole position), and the q-axis is defined in the direction advanced toward the d-axis by ir / 2 degrees of the electrical angle. The magnetic pole position (electrical angle) for the coordinate conversion of the first set is set to the electrical angle 0 based on the phase angle of the U1 phase armature winding of the first set. The magnetic pole position (electrical angle) for the coordinate conversion of the second set is set to the electrical angle 0-ir / 6 based on the phase angle of the U2 phase armature winding of the second set.

[0079]

[0077] The estimation unit 35 converts the three-phase current detection values ​​of the first set iul, ivl, iwl into the d-axis and q-axis current detection values ​​of the first set idl, iql by performing the well-known three-phase to two-phase conversion and rotation coordinate conversion according to the magnetic pole position 0 for the first set based on the angle of phase of the armature winding of phase U1 of the first set. Then, the estimation unit 35 calculates the phase angle 0i of the current vector, based on the d-axis and q-axis current detection values ​​of the first set idl, iql, using equation (24-1). In the case of m phases, the well-known conversion of m phases to two phases and rotation coordinate conversion are performed for current detection values ​​of m phases. [Math. 24] 0: = tan -1 ---(24-1) Vdl / <h2 style=";text-align:left;direction:ltr"> <h2 style=";text-align:left;direction:ltr"> 0i = tan<h2 style=";text-align:left;direction:ltr"> -1 <h2 style=";text-align:left;direction:ltr"> • • • (24 - 2)<h2 style=";text-align:left;direction:ltr"> <h2 style=";text-align:left;direction:ltr"> ^<h2 style=";text-align:left;direction:ltr"> l <h2 style=";text-align:left;direction:ltr"> d2'<h2 style=";text-align:left;direction:ltr"> <h2 style=";text-align:left;direction:ltr">

[0080]

[0078] <h2 style=";text-align:left;direction:ltr"> Alternatively, the estimation unit 35 may convert the second set three-phase current detection values ​​iu2, iv2, iw2 into the second set d-axis and q-axis current detection values ​​id2, iq2 by performing the well-known three-phase to two-phase conversion and rotation coordinate conversion according to the magnetic pole position O-ir / 6 for the second set based on the phase angle of the phase armature winding U2 of the second set. Then, the estimation unit 35 may calculate the phase angle 0i of the current vector, based on the second set d-axis and q-axis current detection values ​​id2, iq2, using equation (24-2).Taking into account the variation between the two sets, the phase angle 0i of the current vector of each set can be calculated, the phase angle 0v of the voltage vector of each set can be calculated, and these can be used for calculating the applied voltage estimation values ​​of each set.

[0081]

[0079] Alternatively, the estimation unit 35 may calculate the phase angle 0i of the current vector, based on the d-axis and q-axis current detection values ​​of the first set idl, iql and the d-axis and q-axis current detection values ​​of the second set id2, iq2, using equation (25). Using the total of the currents, the harmonic wave component included in the currents may be removed. [Math. 25] 6j = tan 1 -r-----7— ' ' * (25) + l d2' The estimation unit 35 calculates d-axis and q-axis applied voltage estimation values ​​of the first set Vdl_alt, Vql_alt and d-axis and q-axis applied voltage estimation values ​​of the second set Vd2_alt, Vq2_alt, based on the voltage vector phase angle 0v, using equation (26). [Math. 26] fVdl_alt Valt COS 3V I Vql_alt ^alt SÎD 3V , . < Vd2_alt =Valt COS 6V ' " <Vq2_alt ^alt SÎB 3V

[0083]

[0081] Herein, Vdl_alt is an estimate value of d-axis applied voltages of the first set, Vql_alt is an estimate value of q-axis applied voltages of the first set, Vd2_alt is an estimate value of d-axis applied voltages of the second set, Vq2_alt is an estimate value of q-axis applied voltages of the second set. The estimate values ​​of applied voltages of each set are calculated in the d-axis and q-axis coordinate system. Valt is a voltage amplitude.

[0084]

[0082] The estimation unit 35 calculates the voltage amplitude Valt using equation (27). In the case of 1-pulse control, it can be roughly defined as k=^6 / n. In a region in which the induced voltage which is a product of the electric angle velocity co and the magnetic flux rp is small, since the applied voltage becomes located between 120-degree excitation and 180-degree excitation, k can be defined by a value smaller than ^6 / n, based on the amplitude ratio of the fifth-order electric angle component to the first-order electric angle component. [Math. 27] Valt = kV dc • • • (27)

[0085]

[0083] As shown in [Fig. 13], the amount of phase angle shift a is determined on the basis of the amplitude ratios 15 / 11 between the amplitude 15 of the fifth-order electrical angle component and the amplitude II of the first-order electrical angle component, and the relative phase angle A05-5A01 of the fifth-order electrical angle component with respect to the phase angle A01 of the first-order component of electric angle calculated by equation (9).

[0086]

[0084] As shown in equation (28), using a phase angle shift amount calculation function fa in which a relationship between the amplitude ratio between the amplitude I2m-1 of the (2m-1)-th order electrical angle component and the amplitude II of the first order electrical angle component, the relative phase angle of the (2m-1)-th order electrical angle component with respect to the phase angle A01 of the first order electrical angle component, and the phase angle shift amount a is preliminarily defined, the estimation unit 35 calculates the phase angle shift amount a on the basis of the amplitude I2m-1 of the (2m-1)-th order electrical angle component,of the amplitude II of the first-order component of electric angle and the relative phase angle of the (2m-l)-th order component of electric angle with respect to the phase angle A01 of the first-order component of electric angle, which are calculated based on the current detection value of each phase. As the phase angle displacement amount calculation function fa, mapping data is used or a high-order function is used. , [Math. 28] a = -(2m- tm) ---(28)

[0087]

[0085] Alternatively, if the relative phase angle of the (2m-l)-th order electrical angle component with respect to the phase angle A01 of the first order electrical angle component is calculated, arc tangent calculation is necessary as shown in Equation (18). The arithmetic processing load therefore becomes large. If three-dimensional mapping data is used for the phase angle displacement amount calculation function fa, the storage capacity becomes large. The voltage equation in a steady state can be approximated by Equation (29) at high speed. If the square sum of the d-axis voltage Vd and the q-axis voltage Vq is constant, the q-axis current increases with the reduction of 0v. [Math. 29] f V d = -œL q I q q q • • • (29^ V q = w(L d I d + (p) To prevent an absolute value of bus current from becoming excessive, it is better to broadly estimate the phase angle 0v of the applied voltage estimation values ​​used when switching to inverter control. In [Fig. 13], if the maximum value of the phase angle shift amount a at each amplitude ratio is extracted, a relationship between the amplitude ratio and the phase angle shift amount a (the maximum value of the phase angle shift amount a at each amplitude ratio) is obtained as shown in [Fig. 14].

[0089]

[0087] Therefore, as shown in equation (30), using a phase angle displacement amount calculation function fa in which a relationship between the amplitude ratio between the amplitude I2m-1 of the (2m-1)-th order electrical angle component and the amplitude II of the first order electrical angle component, and the phase angle displacement amount a is preliminarily defined, the estimation unit 35 can calculate the phase angle displacement amount a on the basis of the amplitude I2m-1 of the (2m-1)-th order electrical angle component and the amplitude II of the first order electrical angle component, which are calculated on the basis of the current detection value of each phase. As the phase angle displacement amount calculation function fa, mapping data is used or a high-order function is used.In this case, in the estimation unit 35, the estimation values ​​of applied voltages can be calculated without calculating the phase angle A01 of the first-order component of electrical angle and the phase angle 02m-1 of the (2m-1)-th-order component of electrical angle. [Math. 30] ---(30) vh /

[0090]

[0088] In equation (26), the d-axis and q-axis applied voltage estimation values ​​of each set are calculated, the applied voltage estimation value of each phase of each set can be calculated. For example, the estimation unit 35 can calculate the applied voltage estimation values ​​Vul_alt, Vvl_alt, Vwl_alt of three phases of the first set, based on the magnetic pole position 0 for the first set, the phase angle 0v of the applied voltage vector, and the DC voltage Vdc using equation (31). For example, the estimation unit 35 can calculate the applied voltage estimation values ​​Vu2_alt, Vv2_alt, Vw2_alt of three phases of the second set, based on the magnetic pole position 0 for the first set, the phase angle 0v of the applied voltage vector, and the DC voltage Vdc using equation (31). magnetic pole 0-ir / 6 for the second set, the phase angle 0v of the applied voltage vector, and the DC voltage Vdc using equation (32). In the case of m phases, the applied voltage estimation values ​​of m phases are calculated by the similar calculation method taking into account the phase angle of each phase. [Math. 31] ( When 05 1 IA 05 A 05 + bj| $ Z Valait Vdc | When 77 31T 6V + — < 9 < 3V + — Z Z Valait 0 77 2n 77 271 ( When 05 1 + W | IA 05 A 05 ^3 + 2^ g” Vv^_alf Vdc 1 When 77 2n 377 277 05 -+ toi + w | IA CD A 05 + + Vvl aU = 0 Z 3 77 2tt 77 277 ( When 05 1 bJ 1 1 w | IA 05 A 05 'S + ' Kvl_aZt Vdc 1 \ A H n 2n 377 277 1 When 05 + bJ | 1 W | IA 05 A 05 2 g” ' Vwi_ait 0 • • -(31) [Math.32] f When 77 77 T7 O> 1 ixj | : IA 05 1 051 : A 05 'S + 2 ' Vu2_alt V^ [ When 77 77 3n 05 + bJ| IA 05 1 CN A ,05 + 2 ' VU2_alt 0 77 277 77 77 277 ( When 05 1 N>| + w | IA 05 1 Ch| A 3” TT \ Vv2_alt — V([c Lt O 1 When 77 277 77 377 277 V |5O 1 05 VI | in + 1 CM + £ 05 0v+^“ + ^“' Vv2 ai = Z 6 77 277 77 77 277 ( When 05 1 to| 1 w | IA 05 1 0^1 A 3” > Vw2_alt Vdc 1 1 to {I 77 277 77 3t7 2h ( When 05 « + bJ| 05 1 05 | A 2 ' Vw2_alt 0 .

[0091]

[0089] The estimation unit 35 can then convert the applied voltage estimation values ​​of three phases of the first set Vul_alt, Vvl_alt, Vwl_alt into values d-axis and q-axis applied voltage estimation values ​​of the first set Vdl_alt, Vql_alt, by performing the well-known three-phase to two-phase conversion and rotation coordinate conversion based on the magnetic pole position 0 for the first set. The estimation unit 35 can convert the three-phase applied voltage estimation values ​​of the second set Vu2_alt, Vv2_alt, Vw2_alt into d-axis and q-axis applied voltage estimation values ​​of the second set Vd2_alt, Vq2_alt, by performing the well-known three-phase to two-phase conversion and rotation coordinate conversion based on the magnetic pole position O-ir / 6 for the second set. In the case of m phases, the well-known m-phase to two-phase conversion and rotation coordinate conversion are performed for the m-phase applied voltage estimation values.

[0092]

[0090] <Estimation de courant de bus> The estimation unit 35 can estimate a bus current Idc flowing in the bus line which connects between the inverter of the first set 5a and the inverter of the second set 5b, and the DC power source 2.

[0093]

[0091] The bus current Idc is given by a sum of a bus current Idcl of the inverter of the first set, a bus current Idc2 of the inverter of the second set and a bus current Idc3 of the converter, as shown in equation (33). [Math. 33] Idc ~ Idcl + Idc2 + Idc3 ' ' ' (33)

[0094]

[0092] If the armature current takes an ideal form including only the first-order component of electrical angle, the current iul of phase Ul, the high-potential side switching device SPul of phase U1, and the bus current Idcl of the inverter of the first set become as shown in [Fig. 15], and the bus current Idcl is given by equation (34). At this point, an average value of Idcl becomes -0.95511. [Math. 34] ^dcl iulSpul + + iwl^pw! ^ul^nul ^vl^nvl ^wl^nwl (^4) It is assumed herein that SPul, SPvl, ... become 1 when the corresponding switching device is activated, and become 0 when the switching device is deactivated.

[0096]

[0094] On the other hand, if the armature current takes an ideal form including the fifth-order electrical angle component in addition to the first-order electrical angle component, the current iul of phase Ul, the high-potential side switching device SPul of phase Ul, and the bus current Idcl of the inverter of the first set become as shown in [Fig. 16], and the average value of Idcl becomes -0.93611.

[0097]

[0095] Then, as shown in equation (35) or equation (36), the estimation unit 35 calculates the bus current Idc by the sum of products of the current detection values ​​of the armature windings and the estimation values ​​of applied voltages, and a product of the field current detection value if and the instruction value of field voltages Vf, and dividing the sum by the DC voltage Vdc. With the calculation according to this method, it is possible to calculate the bus current Idc with good accuracy by taking into account the influence of the fifth-order component of electrical angle. [Math. 35] 1 Idc 77 + ^vl^vl_alt + ^wl^wl_alt vdc ~^^u2^u2_alt + ^v2^v2_alt + ^w2^w2_alt + ' (35) [Math. 36] 1 Idc — 77 \Idl^dl_alt + IqlVql_alt + Id2^d2_alt vdc Iq2Vq2_alt + îfVf) ^(36)

[0098]

[0096] Herein, iul, ivl, iwl, iu2, iv2, iw2 are the current detection value of each phase of each set, idl, iql, id2, iq2 are the d-axis and q-axis current detection values ​​of each set, as described below.

[0099]

[0097] 1-5-4. Inverter control unit 36 When the control switching determination unit 33 determines that the inverter control is to be executed, the inverter control unit 36 ​​executes the inverter control.

[0100]

[0098] For each set, the inverter control unit 36 ​​calculates basic voltage command values, based on current command values ​​of the armature winding, and electrical constants of the rotating electric machine 1, and calculates voltage command values, based on the basic voltage command values. The inverter control unit 36 ​​then turns on and off the plurality of inverter switching devices of each set, based on the voltage command value of each set, and applies voltages to the three-phase armature windings of each set.

[0101]

[0099] In the present embodiment, for each set, the inverter control unit 36 ​​calculates the current command values ​​of the armature winding, based on the output command value and the electrical angle speed co. The DC voltage Vdc can also be taken into account. A well-known vector control is used, and the d-axis and q-axis current command values ​​Id*, Iq* are calculated for each set. In the present embodiment, the d-axis and q-axis current command values ​​Idl*, Iql* of the first set and the d-axis and q-axis current command values ​​Id2, Iq2* of the second set generally become equal values.

[0102]

[0100] The inverter control unit 36 ​​converts the three-phase current detection values ​​of the first set iul, ivl, iwl into the d-axis and q-axis current detection values ​​of the first set idl, iql by performing the well-known three-phase to two-phase conversion and rotation coordinate conversion according to the magnetic pole position 0 for the first set. The inverter control unit 36 ​​converts the three-phase current detection values ​​of the second set iu2, iv2, iw2 into the d-axis and q-axis current detection values ​​of the second set id2, iq2 by performing the well-known three-phase to two-phase conversion and rotation coordinate conversion according to the magnetic pole position 0-ir / 6 for the second set.

[0103]

[0101] For each set, the inverter control unit 36 ​​executes feedback control that changes feedback voltage instruction values ​​so that the current detection values ​​approach the current instruction values, and predictive control that calculates the basic voltage instruction values ​​(hereinafter referred to as predictive voltage instruction values) on the basis of the current instruction values ​​and the electrical constants of the rotating electric machine 1; and calculates the basic voltage instruction values. voltage by adding the feedback voltage instruction values ​​and the predictive voltage instruction values.

[0104]

[0102] In the present embodiment, as shown in equation (37), the inverter control unit 36 ​​calculates the d-axis and q-axis voltage command values ​​of the first set Vdl, Vql by adding the d-axis and q-axis predictive voltage command values ​​of the first set Vdffl, Vqffl and the d-axis and q-axis feedback voltage command values ​​of the first set Vdfbl, Vqfbl. The inverter control unit 36 ​​calculates the d-axis and q-axis voltage command values ​​of the second set Vd2, Vq2 by adding the d-axis and q-axis predictive voltage command values ​​of the second set Vdff2, Vqff2 and the d-axis and q-axis feedback voltage command values ​​of the second set Vdfb2, Vqfb2. [Math. 37] = Vdffi + Vdfbl Vql = Vqffi + Vqfbi Vd2=Vdff2 + Vdfb2 <Vq2 = Vqff2 + Vqfb2

[0105]

[0103] As feedback control, for each set, the inverter control unit 36 ​​performs PI control based on a deviation between the d-axis current instruction value Id* and the d-axis current detection value id, and the like, and calculates the d-axis feedback voltage instruction value Vdfb; and performs PI control based on a deviation between the d-axis current instruction value Id* and the d-axis current detection value id, and the like, and calculates the d-axis feedback voltage instruction value Vdfb; q-axis current Iq* and q-axis current detection value iq, and the like, and calculates the q-axis feedback voltage instruction value Vqfb. Feedback control may not be realized.

[0106]

[0104] As a predictive control, as in patent document 2, the d-axis and q-axis predictive voltage instruction values ​​of each set are calculated by equation (38). If the mutual inductance is large, an equation considering the mutual inductance can be used. [Math. 38]

[0107] ^d Ld V dffl V qffl- V dff2 Vqff2. 0 Tcc 0 L q T 1 ce J Lq T 1 ce- 1

[0105] Idl *■ Jq^ J Id2 l q2 *■ CL rrt CC u>Ld L d CL rrt *cc ^d —a)L n H CL rrt * ce ~^q CL rrt 1 CC 1 Idrl I i Uqr 1J Idr2 Jqr2. Cû(p • • • (38) Cl)(p

[0108]

[0109] Herein, Ld is a d-axis inductance, Lq is a q-axis inductance, q> is an interconnecting flux, and Ra is a resistance value of the armature winding. These are the electrical constants of the rotating electric machine 1. Tcc is a time constant of a target response. Idrl, Iqrl are the d-axis and q-axis current instruction values ​​obtained by performing target response delay processing on Idl*, Iql* respectively (e.g., first-order delay processing with a target response time constant Tcc). Similarly, Idr2, Iqr2 are the d-axis and q-axis current instruction values ​​obtained by performing target response delay processing on Id2*, Iq2* respectively. Target response delay processing may not be performed, but Idl*, Iql* can be used instead of Idrl, Iqrl, and Id2*, Iq2* can be used instead of Idr2, Iqr2.

[0106] The inverter control unit 36 ​​converts the voltage command values of d-axis and q-axis of the first set Vdl, Vql into three-phase voltage instruction values ​​of the first set Vul,Vvl,Vwl by performing the well-known fixed coordinate conversion and the well-known three-phase to two-phase conversion according to the magnetic pole position 0 for the first set. The inverter control unit 36 ​​converts the d-axis and q-axis voltage instruction values ​​of the second set Vd2, Vq2 into three-phase voltage instruction values ​​of the second set Vu2, Vv2, Vw2 by performing the well-known fixed coordinate conversion and the well-known conversion of three phases into two phases depending on the magnetic pole position O-ir / 6 for the second set. Modulation that does not change the line voltages, such as two-phase modulation or space vector modulation, can be added to the three-phase voltage instruction values ​​of each set.

[0107] The inverter control unit 36 ​​controls the activation / deactivation of the plurality of communication devices of the inverter of the first set 5a, based on the three-phase voltage instruction values ​​of the first set Vul,Vvl,Vwl. The inverter control unit 36 ​​controls the activation / deactivation of the plurality of communication devices of the second set inverter 5b, based on the three-phase voltage instruction values ​​of the second set Vu2, Vv2, Vw2. The well-known carrier comparison PWM control or the well-known space vector PWM control is used for the PWM control.

[0110]

[0108] <Définition de valeurs d’instruction de tension au moment de la commutation>At the time of switching from alternator generation control to inverter control, the inverter control unit 36 ​​calculates the base voltage command values ​​(in this example, the predictive voltage command values) of each set, based on the estimated values ​​of voltages applied when the alternator generation control is executed. [YES]

[0109] According to this configuration, even if there is an error of the base voltage instruction values ​​due to an error of the electrical constants, since the base voltage instruction values ​​are calculated on the basis of the estimation values ​​of applied voltages calculated just before the end of the alternator generation control at the time of switching from the alternator generation control to the inverter control, a deviation between the applied voltage and the base voltage instruction value at the time of switching can be reduced, and the variation of the bus current can be reduced.

[0112]

[0110] For example, the inverter control unit 36 ​​sets the base voltage command values ​​to the applied voltage estimation values ​​at the time of switching and, after switching, gradually changes the base voltage command values ​​from the applied voltage estimation values ​​to the base voltage command values ​​set on the basis of the current command values ​​and the electrical constants.

[0113] [YES] In the present embodiment, after switching, using the first equation of equation (39), the inverter control unit 36 ​​gradually changes the d-axis and q-axis predictive voltage instruction values ​​of the first set Vdffl_sw, Vqffl_sw from the d-axis and q-axis applied voltage estimation values ​​of the first set Vdl_alt, Vql_alt to the d-axis and q-axis predictive voltage instruction values ​​of the first set Vdffl, Vqffl set on the basis of the current instruction values ​​and the constants electrical constants. After switching, using the second equation of equation (39), the inverter control unit 36 ​​gradually changes the second set d-axis and q-axis predictive voltage instruction values ​​Vdff2_sw, Vqff2_sw from the second set d-axis and q-axis applied voltage estimation values ​​Vd2_alt, Vq2_alt to the second set d-axis and q-axis predictive voltage instruction values ​​Vdff2, Vqff2 set based on the current instruction values ​​and electrical constants. Herein, a switching coefficient Ksw is set to 1 at the time of switching, and gradually decreases to 0 after switching.Until the switching coefficient Ksw changes from 1 to 0 after switching, in equation (37), the d-axis and q-axis predictive voltage instruction values ​​of the first set Vdffl_sw, Vqffl_sw and the d-axis and q-axis predictive voltage instruction values ​​of the second set Vdff2_sw, Vqff2_sw calculated by equation (39) are used. [Math. 39] Vdff l_sw Vl l_alt Vqff 1_SW - ^sw Vql_a.lt ^dff2_sw = K V12_alt Vqff2_sw. 1YSW Vq2_alt •(39)

[0114]

[0112] The switching coefficient Ksw can be set to 1 for a predetermined period after switching, and then reduced to 0. A reduction slope of the switching coefficient Ksw may not be constant, but can be defined by any waveform. The switching coefficient Ksw can change gradually from 1 to 0.

[0115]

[0113] <Moteur générateur pour véhicule> The rotating electric machine 1 can serve as a motor generator for a vehicle. For example, as shown in [Fig. 17], the rotational axis of the rotor of the rotating electric machine 1 is connected to a crankshaft of an internal combustion engine 100 via a pulley and belt mechanism 101. The rotational axis of the rotating electric machine 1 is connected to wheels 103 via the internal combustion engine 100 and a transmission 102.

[0116]

[0114] The rotating electric machine 1 operates as a starting motor and a torque assist motor at the time of starting the internal combustion engine 100 and at the time of torque assist to assist the output of the engine. internal combustion engine 100; and also functions as a charging generator that charges the DC power source 2 after the internal combustion engine is started. The inverter control and the alternator generation control are switched according to the operating state. Since the current disturbance at the time of switching causes the variation of the output torque, it may cause the variation of the motive force of the vehicle. At the time of switching from the alternator generation control to the inverter control, by calculating the basic voltage instruction values ​​of each set used for the inverter control based on the estimation values ​​of voltages applied when the alternator generation control is executed, the variation of the motive force of the vehicle can be suppressed and the driving pleasure of the driver can be improved.

[0117]

[0115] 2. Embodiment 2 The rotating electric machine 1 and the control device 30 according to embodiment 2 will be explained below. The constituent parts identical to those of embodiment 1 are not described below. The basic configuration of the rotating electric machine 1 and the control device 30 according to the present embodiment is the same as that of embodiment 1. Embodiment 2 is different from embodiment 1 in that m is defined as 4 and by the associated configuration.

[0118]

[0116] In the present embodiment, m is set to 4. The stator 18 is provided with four-phase armature windings Cul, Cvl, Cwl, Cxl of phase Ul, phase VI, phase Wl, phase XI of the first set, and four-phase armature windings Cu2, Cv2, Cw2, Cx2 of phase U2, phase V2, phase W2, phase X2 of the second set.

[0119]

[0117] In the present embodiment, as schematically shown in [Fig. 18], the phase angle difference X of the electrical angle of the phase angles of the four-phase armature windings Cu2, Cv2, Cw2, Cx2 of the second set with respect to phase angles of the four-phase armature windings Cul, Cvl, Cwl, Cxl of the first set is set to ir / 4 (45 degrees).

[0120]

[0118] Although the illustration is omitted, the inverter of the first set 5a is further provided with the series circuit of the high-potential-side switching device and the low-potential-side switching device for phase XI; and the series circuit for phase XI is connected to the armature winding of phase XL. Although the illustration is omitted, the inverter of the second set 5b is further provided with the series circuit of the high-potential-side switching device and the low-potential-side switching device for phase X2; and the series circuit for phase X2 is connected to the armature winding of phase X2.

[0121]

[0119] The first set armature current sensor 8a further detects a current ixl flowing in the armature winding of phase XL. The armature current detection unit 32 further detects a current detection value ixl flowing in the armature winding of phase XI, based on the output signal of the first set armature current sensor 8a. The second set armature current sensor 8b further detects a current ix2 flowing in the armature winding of phase X2. The armature current detection unit 32 further detects a current detection value ix2 flowing in the armature winding of phase X2, based on the output signal of the second set armature current sensor 8b.

[0122]

[0120] <Explication de principe de l’estimation de tension et de la définition d’angle de phase> In the alternator generation control, the DC voltage Vdc applied to the armature winding of each phase becomes 1 pulse which is turned on or off every 180 degrees, and becomes similar to the state in which 1 pulse control is performed. Therefore, the current of each phase of each set becomes a waveform in which a harmonic wave of the third-order component of electrical angle is superimposed on a fundamental wave of a first-order component of electrical angle. The current of each phase of each set is given by equation (40). [Math. 40] 4i = sin(<ï)t + ^) + I3 sin(3éot + 52) / n\ / TT 4i = 4 sin (a)t + Si — — ) 4- / 3 sin (3a)t 4- 52 4- — iwl = 4 sin(éot 4- <4 4- tt) 4- / 3 sin(3û)t 4- 52 + tt) / TT 4- / 3 sin ( 3 4- 52 — — U <h2 style=";text-align:left;direction:ltr"> / 3\ / TT<h2 style=";text-align:left;direction:ltr"> <h2 style=";text-align:left;direction:ltr"> iv2 = 4 sin ( — 7^ + / 3 sin ( + ô2 — —<h2 style=";text-align:left;direction:ltr"> <h2 style=";text-align:left;direction:ltr"> / 3\ / TT<h2 style=";text-align:left;direction:ltr"> <h2 style=";text-align:left;direction:ltr"> iw2 = 4 sin I cot 4- (Sj 4- -tt ) 4- / 3 sin ( 3wt 4- Ô2 4- —<h2 style=";text-align:left;direction:ltr"> <h2 style=";text-align:left;direction:ltr"> ix2 = 4 sin (4" ^1 4" 7) 4" / 3 sin 3cot 4- ô2 4- -tt<h2 style=";text-align:left;direction:ltr"> <h2 style=";text-align:left;direction:ltr">

[0123]

[0121] <h2 style=";text-align:left;direction:ltr"> Herein, Il is a current magnitude of the first-order electrical angle component, 13 is a current magnitude of the third-order electrical angle component, ôl is a phase angle relative to a current phase angle eut of the first-order electrical angle component, ô2 is a phase angle relative to a current phase angle 3cot of the third-order electrical angle component. For expression by the vector diagram, the first-order electrical angle component of the current of each phase of each set has a phase angle relationship which is shown in [Fig. 19], and the third-order electrical angle component of the current of each phase of each set has a phase angle relationship which is shown in [Fig.20],

[0124]

[0122] iu2-iv2 is deduced as in equation (41) from equation (40). Herein, 2cos(ir / 4) =^2. [Math. 41] TT iu2 - iv2 = h Sin(wt + SJ 2 cos- — / 3 sin(3â)t 4-52) 2 cos— ---(41) 4

[0125]

[0123] When deforming using equation (41) and the first equation of equation (40), the first-order component of electric angle iul_l and the third-order component of electric angle iul_3 of the current iul of phase U1 of the first set can be expressed by the following equation. [Math. 42]

[0126] 1 iui_i = h sm(ü)t + = -yu± + ^u2 ^v2 2 COS-r 4 7 1 iui_3 = h sin(3ûJt + 52) = iul -

[0124] 1 / 2 VU1 + O2 ^v2\ • • • (42) O2 02\ V2

[0127] As shown in Equation (41) and [Fig. 19], the first-order electric angle component of iu2-iv2 becomes ^2 times the first-order electric angle component of iul. As shown in Equation (41) and [Fig. 20], the third-order electric angle component of iu2-iv2 becomes -^2 times the third-order electric angle component of iul. Therefore, as shown in the first equation of Equation (42), by adding (iu2-iv2) / V2 to iul, and dividing by 2, the third-order electric angle component of iul can be canceled, and the first-order electric angle component of iul can be extracted. As shown in the second equation of equation (42), by subtracting (iu2-iv2) / 'V2 from iul, and dividing by 2, the first-order electric angle component of iul can be canceled, and the third-order electric angle component of iul can be extracted.

[0125] iw2-iv2 is deduced as in equation (43) from equation (40). Herein, 2cos(ir / 4) =^2. [Math. 43]

[0128] / TC\ 71 i W 2 - = h sinl + -I 2cos- \ Zz 4 / n\ n — I3 sin (3a)t + 52 + ) 2 cos — • • • (43)

[0126] When deforming using equation (43) and the fourth equation of equation (40), the first-order electrical angle component ixl_l and the third-order electrical angle component ixl_3 of the current ixl of phase XI of the first set can be expressed by the following equation. [Math. 44] ( / n hu — h sin + ^i+^ < ^i_3 = h sin ( 3mt + Ô2 + -k __ 1 I. ^mz2__-i / . ^w2 ^v2\ - 2 ) + ~ tT I 7 vx1 ) Z 2 COS-F z v V2 / k 4 7 _ 1 I . iw2 if2 I _ (. Îw2 Îv2\ = ^V'1 “ J X. J • • • (44)

[0129]

[0127] As shown in Equation (43) and [Fig. 21], the first-order electric angle component of iw2-iv2 becomes ^2 times the first-order electric angle component of ixl. As shown in Equation (43) and [Fig. 22], the third-order electric angle component of iw2-iv2 becomes -^2 times the third-order electric angle component of ixl. Therefore, as shown in the first equation of Equation (44), by adding (iw2-iv2) / V2 to ixl, and dividing by 2, the third-order electric angle component of ixl can be canceled, and the first-order electric angle component of ixl can be extracted. As shown in the second equation of Equation (44), by subtracting (iw2-iv2) / V2 from ixl, and dividing by 2, the first-order electric angle component of ixl can be canceled, and the third-order electric angle component of ixl can be extracted.

[0130]

[0128] Herein, the phase angle of ixl in equation (44) advances by ir / 2 relative to the phase angle of iul. As shown in equation (45), when the sine in equation (44) is converted to a cosine, equation (44) becomes the cosine version of iul. [Math. 45] / 3 cos(3eot + Ô2)

[0131]

[0129] Therefore, as shown in equation (46), based on the first-order electrical angle component of iul in the first equation of equation (42), and the first-order electrical angle component of ixl in the first equation of equation (44), the amplitude II and the phase angle A01 of the first-order electrical angle component of iul can be calculated. [Math. 46]

[0132] ' A#! = had + = tan 1 Z xsin(û)t + li cosÇcoût + • • ■ (46)

[0130] kt2 ^v2 \ V2 / As shown in Equation (47), based on the third-order electrical angle component of iul in the second equation of Equation (42), and the third-order electrical angle component of ixl in the second equation of Equation (44), the amplitude 13 and phase angle A03 of the third-order electrical angle component of iul can be calculated. [Math. 47] Z3 = V(Zi sin(3wt + Ô2W + (71 cos(3wt + 52)) 2

[0133] ^u2 ^v2\ ^w2 ^v2\ ' A03 = 3a)t + Ô2 = tan 1 I r sin(3eat + 52) Zi cos(3a)t + 52) • • • (47) iul = tan 1 Îu2 Îy2 \ V2 ^w2 ^v2 I V2 /

[0131] From the second equation of equation (46) and the second equation of equation (47), a relative phase angle A03-3A01 of the third-order component of electrical angle with respect to the phase angle A01 of the first-order component of electrical angle is given by equation (48). [Math. 48]

[0134]

[0135] △03 - 3A0! = ô2 - 3^ _ iu2 Îy2 111 Æ _ Îw2 Îy2 X1 V2

[0132] Equation (49) is obtained by squaring each of the first equation and the second equation of Equation (42). Therefore, by performing low-pass filter processing on each of the first equation and the second equation of Equation (49), a square of the amplitude II of the first-order component of electric angle and a square of the amplitude 13 of the third-order component of electric angle can be calculated. Without using Equation (45) of ixl whose phase angle advances by ir / 2 with respect to the phase angle of iul as in Equation (46) and Equation (47), the amplitude II of the first-order component of electric angle and the amplitude 13 of the third-order component of electric angle can be calculated only by Equation (42) of iul. [Math. 49] 2tui i2 = h2 [1 “ cos{2(<ï)t + ^)}] = ~(iul + 2^32 =^2[l-cos{2(3ûit + 0] k 4 \ V2

[0133] <Généralisation du résultat de déduction>

[0136] In the above, when m=4, the equations were deduced for iul of phase U1 and ixl of phase XI whose phase angle advances by ir / 2 with respect to the phase angle of iul. This deduction result will be generalized.

[0134] Assuming that the phase angle difference between the armature windings of the first set and the armature windings of the second set is X, as shown in equation (50), phase angle lagging amounts of phase U2, phase V2, phase W2, and phase X2 of the second set relative to phase U1 become X, X+ir / 2, X-ji, and X-ji / 2, respectively. As shown in equation (51), by making the phase angle difference between phase V2 and phase W1 equal to the phase angle difference X between phase U1 and phase U2, a vector from V2 to U2 in [Fig. 19] can be made parallel to Ul. Therefore, as shown in equation (52), the phase angle difference X becomes ir / 4 from equation (51). [Math. 50]

[0137]

[0138] [Math. 51] n- + = X ■ - - (51) XZ' [Math. 52] X = J • --(52)

[0135] The minimum phase angle difference AOmin among phases of each set which is a minimum value of phase angle differences greater than 0 between a plurality of phase angles obtained by collecting a phase angle and an inverse phase angle of the armature winding of each phase in each set is ji / 2. The phase angle difference X of the electrical angle between the three-phase armature windings of the first set and the three-phase armature windings of the second set becomes ir / 4 which is 1 / 2 of the minimum phase angle difference AOmin (=ir / 2) among the phases of each set.

[0136] Generalizing this deduction result, when m is an even number, the minimum phase angle difference AOmin among phases of each set which is a minimum value of phase angle differences greater than 0 between a plurality of phase angles obtained by collecting a phase angle and an inverse phase angle of the armature winding of each phase in each set is 2ir / m. The phase angle difference X of the electrical angle between the m-phase armature windings of the first set and the m-phase armature windings of the second set becomes 1 / 2 of the minimum phase angle difference AOmin among the phases of each set, i.e., ir / m.

[0139]

[0137] In the above equation (42), to calculate the first-order electrical angle component and the third-order electrical angle component of the current value iul of phase Ul, the current value iul of phase U1, and the current value iu2 of phase U2 whose phase angle difference from phase Ul is ir / 4 (=ir / m), and the current value iv2 of phase V2 whose phase angle difference from phase Ul is 3ir / 4 (=ir-jr / m) are used.In the above equation (44), to calculate the first-order electrical angle component and the third-order electrical angle component of the current value ixl of phase XI whose phase angle difference from phase Ul is ji / 2, the current value ixl of phase XI, and the current value iw2 of phase W2 whose phase angle difference from phase XI is ir / 4 (=ir / m), and the current value iv2 of phase V2 whose phase angle difference from phase XI is 3ir / 4 (=ir-jr / m) are used.

[0140]

[0138] For generalization purposes, phase Ul is replaced by phase Al which is any phase among the m phases of the first set. Then, equation (42) can be generalized by equation (53) which calculates a first-order component of electric angle ial_l and a (ml)-th order component of electric angle ial_m-l of the current value ial of phase Al. [Math. 53] r. r ■ / । e \ al । «2 ^b2 'al 1 = A Sin(üJt + ^)=- +---—— C0SU ---(53) îai.mi = sin{(m - l) <ot + 52) = cos (—) v xml

[0141]

[0139] Herein, ia2 is a current value flowing through the armature winding of phase A2, among the m phases of the second set, a phase angle difference of which with respect to phase A1 is ir / m. ib2 is a current value flowing through the armature winding of phase B2, among the m phases of the second set, a phase angle difference of which with respect to phase A1 is (ir-ir / m).

[0142]

[0140] Equation (44) and equation (45) can be generalized by equation (54) which calculates the first-order component of electrical angle ibl_l and the (ml)-th order component of electrical angle ibl_m-l of the current value ibl of phase Bl, among the m phases of the first set, whose phase angle difference with respect to phase Al is ji / 2. [Math. 54] / 7T\ ^i_i = h s i n ( + — ) = h cos(éot + ^) = —- + s where ^c2 — *d2 / 7T\ COS — \mj • • • (54) = 7 m _1 cos{(m - l>ù + 52] = y- - cos I — ) \mj

[0143]

[0141] Herein, ic2 is a current value flowing through the armature winding of phase C2, among the m phases of the second set, a phase angle difference of which with respect to phase B1 is ir / m. id2 is a current value flowing through the armature winding of phase D2, among the m phases of the second set, a phase angle difference of which with respect to phase B1 is (ir-ir / m). Phase C2 or phase D2 may be the same as phase A2 or phase B2 depending on the setting value of m. In the case of m= 4, phase D2 may become the same as phase B2.

[0144]

[0142] Equation (46) can be generalized by Equation (55) using Equation (53) and Equation (54). Therefore, the estimation unit 35 calculates the amplitude II and the phase angle A01 of the first-order component of electrical angle, using Equation (55), on the basis of the current detection value ial of phase A1, the current detection value ia2 of phase A2, the current detection value ib2 of phase B2, the current detection value ibl of phase B1, the current detection value ic2 of phase C2, and the current detection value id2 of phase D2. [Math. 55]

[0145]

[0143] Equation (47) can be generalized by Equation (56) using Equation (53) and Equation (54). Therefore, the estimation unit 35 calculates an amplitude Im-1 and a phase angle 0m-1 of the (ml)-th order component of electrical angle, using Equation (56), on the basis of the current detection value ial of phase A1, the current detection value ia2 of phase A2, the current detection value ib2 of phase B2, the current detection value ibl of phase B1, the current detection value ic2 of phase C2, and the current detection value id2 of phase D2. [Math. 56]

[0146]

[0144] Equation (48) can be generalized by Equation (57) using the second equation of Equation (55) and the second equation of Equation (56). Therefore, the estimation unit 35 calculates a relative phase angle of the (ml)-th order component of electrical angle on the basis of the phase angle A01 of the first order component of electrical angle, using Equation (57), on the basis of the current detection value ial of phase A1, the current detection value ia2 of phase A2, the current detection value ib2 of phase B2, the B1 phase current detection value ibl, C2 phase current detection value ic2, and D2 phase current detection value id2. [Math. 57] tod m _ l — (m — 1)A0| = 82 — (m — 1)^ = tan 1 Aal _ ^a2 Îb2\ 2 cos— \mj — (m — 1) tan 1 Aal । ^a2 i-b2\ 2 cos (— \mj ••*(57) ^bl _ ^c2 ^d2 \2 cosO / ibl । iç2 ^d2 ^2

[0147]

[0145] Equation (49) can be generalized to equation (58) using equation (53). Therefore, the estimation unit 35 calculates the first-order electrical angle component ial_l of the current detection value ial of phase A1, using the first equation of equation (53), on the basis of the current detection value ial of phase A1, the current detection value ia2 of phase A2, and the current detection value ib2 of phase B2; and calculates the magnitude II of the first-order electrical angle component, on the basis of a value obtained by passing a square value of the first-order electrical angle component ial_l through a low-pass filter. Herein, the estimation unit 35 calculates a square root of a value obtained by multiplying 2 by the square value of ial_l after the low-pass filter, as the magnitude II of the first-order electrical angle component.The estimation unit 35 calculates the (ml)-th order electrical angle component ial_m-l of the current detection value ial of phase Al, using the second equation of equation (53), on the basis of the current detection value ial of phase Al, the current detection value ia2 of phase A2, and the current detection value ib2 of phase B2; and calculates the magnitude Im-1 of the (ml)-th order electrical angle component, on the basis of a value obtained by passing a square value of the (ml)-th order electrical angle component ial_m-l through a low-pass filter. Herein, the estimation unit 35 calculates a square root of a value obtained by multiplying 2 by the square value of ial_2-l after the low-pass filter, as the magnitude Im-1 of the (ml)-th order electrical angle component. . [Math. 58] < / 21^ 2 = / i 2 [l-C0 S{2(<0t + O] =UV + ~ z \ z cos ' Ziaim-12 = ^m-i2[l “ cos{2((m - l)û)t + 52)}] • • • (58) \ 2 ^al ^a2 ^b2 |

[0148]

[0146] A cutoff frequency of the low-pass filter on the calculation value of the first equation of equation (58) is made less than twice the electrical angle velocity co (electrical angle frequency). A cutoff frequency of the low-pass filter on the calculation value of the second equation of equation (58) is made less than 2x(ml) times the electrical angle velocity co (electrical angle frequency). A first-order delay filter or moving average processing is used as the low-pass filter.

[0149]

[0147] cCalculation of applied voltage estimation values> Calculation of the estimation values ​​of applied voltages when the alternator generation control is executed will be explained below. Similar to embodiment 1, as shown in equation (59), the phase angle Ov of the applied voltage vector in the d-axis and q-axis rotation coordinate system is to be delayed by (jt-a) relative to the phase angle Oi of the current vector in the d-axis and q-axis rotation coordinate system. Herein, a is a phase angle displacement amount. Herein, the phase angle Oi of the current vector is a phase angle of the current vector of the d-axis and q-axis currents of the first set, and a phase angle of the current vector of the d-axis and q-axis currents of the second set. The phase angle Oi of the current vector of the first set and the phase angle Oi of the current vector of the second set become equal. [Math. 59] d v = 0 ; - (tt - a) • • • (59)

[0150]

[0148] The d axis is defined in the direction of the N pole (magnetic pole position), and the q axis is defined in the direction advanced toward the d axis by ir / 2 degrees of the electric angle. The magnetic pole position (electric angle) for coordinate conversion of the first set is set to the electrical angle 0 based on the phase angle of the U1 phase armature winding of the first set. The magnetic pole position (electrical angle) for coordinate conversion of the second set is set to the electrical angle O-ir / 4 based on the phase angle of the U2 phase armature winding of the second set.

[0151]

[0149] The estimation unit 35 converts the current detection values ​​of four phases of the first set iul, ivl, iwl, ixl into the d-axis and q-axis current detection values ​​of the first set idl, iql by performing the well-known four-phase to two-phase conversion and rotation coordinate conversion according to the magnetic pole position 0 for the first set based on the phase angle of the phase armature winding U1 of the first set. Then, the estimation unit 35 calculates the phase angle 0i of the current vector, based on the d-axis and q-axis current detection values ​​of the first set idl, iql, using equation (60-1). In the case of m phases, the well-known m-phase to two-phase conversion and rotation coordinate conversion are performed for the current detection values ​​of m phases. [Math. 60] 0 t = tan -1 pi) ---(60-1) 0 t = tan -1 (^1) • • • (61 - 2)

[0152]

[0150] Alternatively, the estimation unit 35 can convert the second set four-phase current detection values ​​iu2, iv2, iw2, ix2 into the second set d-axis and q-axis current detection values ​​id2, iq2 by performing the well-known four-phase to two-phase conversion and rotation coordinate conversion according to the magnetic pole position O-ir / 4 for the second set based on the phase angle of the phase armature winding U2 of the second set. Then, the estimation unit 35 can calculate the phase angle 0i of the current vector, based on the second set d-axis and q-axis current detection values ​​id2, iq2, using equation (60-2).Taking into account the variation between the two sets, the phase angle 0i of the current vector of each set can be calculated, the phase angle 0v of the voltage vector of each set can be calculated, and these can be used for calculating the applied voltage estimation values ​​of each set. Alternatively, the estimation unit 35 may calculate the phase angle 0i of the current vector, based on the d-axis and q-axis current detection values ​​of the first set idl, iql and the d-axis and q-axis current detection values ​​of the second set id2, iq2, using equation (61). Using the total of the currents, the harmonic wave component included in the currents may be removed. [Math. 61] 0t = tan -1 (' ql + lq2} ■ ■ ■ (61) + l d2'

[0154]

[0152] The estimation unit 35 calculates d-axis and q-axis applied voltage estimation values ​​of the first set Vdl_alt, Vql_alt and d-axis and q-axis applied voltage estimation values ​​of the second set Vd2_alt, Vq2_alt, based on the voltage vector phase angle 0v, using equation (62). [Math. 62] fri ait Valt COS 3V I Vqlalt ^alt Sin 9V , . ' Vd2.alt = Valt COS 0V <Vq2_alt Valt SÎH 6V

[0155]

[0153] Herein, Vdl_alt is an estimate value of d-axis applied voltages of the first set, Vql_alt is an estimate value of q-axis applied voltages of the first set, Vd2_alt is an estimate value of d-axis applied voltages of the second set, Vq2_alt is an estimate value of q-axis applied voltages of the second set. The estimate values ​​of applied voltages of each set are calculated in the d-axis and q-axis coordinate system. Valt is a voltage amplitude.

[0156]

[0154] The estimation unit 35 calculates the voltage amplitude Valt using equation (63). In the case of 1-pulse control, it can be roughly defined as k=^6 / n. In a region in which the induced voltage which is a product of the electric angle velocity co and the magnetic flux rp is small, since the applied voltage becomes located between 120-degree excitation and 180-degree excitation, k can be defined by a value smaller than ^6 / n, based on the amplitude ratio of the third-order electric angle component to the first-order electric angle component. [Math. 63] Vait = kV dc • • • (63)

[0157]

[0155] Similar to embodiment 1, the phase angle displacement amount a is determined based on the amplitude ratios 13 / 11 between the amplitude 13 of the third-order electrical angle component and the amplitude II of the first-order electrical angle component, and the relative phase angle A03-3A01 of the third-order electrical angle component with respect to the phase angle A01 of the first-order electrical angle component calculated by equation (48).

[0158]

[0156] As shown in equation (64), using a phase angle shift amount calculation function fa in which a relationship between the amplitude ratio between the amplitude Im-1 of the (ml)-th order electrical angle component and the amplitude II of the first order electrical angle component, the relative phase angle of the (ml)-th order electrical angle component with respect to the phase angle A01 of the first order electrical angle component, and the phase angle shift amount a is preliminarily defined, the estimation unit 35 calculates the phase angle shift amount a on the basis of the amplitude Im-1 of the (ml)-th order electrical angle component, the amplitude II of the first order electrical angle component, and the relative phase angle of the (ml)-th order electrical angle component with respect to the phase angle A01 of the first order electrical angle component,which are calculated based on the current detection value of each phase. As the phase angle displacement amount calculation function fa, mapping data is used or a high-order function is used. , [Math. 64]

[0159]

[0157] Alternatively, similarly to embodiment 1, as shown in equation (65), using a phase angle shift amount calculation function fa in which a relationship between the amplitude ratio between the amplitude Im-1 of the (ml)-th order component of electric angle and the amplitude II of the first order component of electric angle, and the phase angle shift amount a is preliminarily defined, the unit estimation unit 35 can calculate the phase angle displacement amount a on the basis of the amplitude Im-1 of the (ml)-th order component of electrical angle and the amplitude II of the first order component of electrical angle, which are calculated on the basis of the current detection value of each phase. As the phase angle displacement amount calculation function fa, mapping data is used or a high-order function is used. In this case, in the estimation unit 35, the estimation values ​​of applied voltages can be calculated without calculating the phase angle A01 of the first order component of electrical angle and the phase angle 0m-1 of the (ml)-th order component of electrical angle. [Math. 65] ---(65) \ M /

[0160]

[0158] In equation (62), the d-axis and q-axis applied voltage estimation values ​​of each set are calculated, but the applied voltage estimation value of each phase of each set can be calculated. For example, the estimation unit 35 can calculate the applied voltage estimation values ​​Vul_alt, Vvl_alt, Vwl_alt, Vxl_alt of four phases of the first set, based on the magnetic pole position 0 for the first set, the phase angle 0v of the applied voltage vector, and the DC voltage Vdc using equation (66). For example, the estimation unit 35 can calculate the applied voltage estimation values ​​Vu2_alt, Vv2_alt, Vw2_alt, Vx2_alt of four phases of the second set, based on the magnetic pole position 0-ir / 4 for the second set, the phase angle 0v of the applied voltage vector, and the DC voltage Vdc using equation (67).In the case of m phases, the applied voltage estimation values ​​of m phases are calculated by the similar calculation method taking into account the phase angle of each phase. [Math. 66] When ev-^<e <ev + ^ vul alt - = ^c ti 3tt When e„ + -<9 <ev +—' vulalt < ti ti Ti Tl = 0 When 9v-- + -<e<9v + - + -, LL L L Tl Tl 3ll 71 ^vl_alt = ^dc When 9V + - + - < e < 9V + — + y, 1 / Z Z Z ' When 9v-^-n<9 <9v+--ti, 1 Z | Tl 3ti Vwl_alt — ^dc 1 When 9v + --it<e <9v + --K' f Tl Tl Tl Tl ( When 9v----<9 <9V+---, 1 Z Z, Z Z ^xl_alt — ^dc ) u / u Tl Tl 3n Tl When 9v+---<9 <9v + — ~-, \ LL L l. Math. 67] z n Tl Tl ^xl_alt — 0 • • • (66) When 0v--<e--<ev+y.<h2 style=";text-align:left;direction:ltr">vu2_ait = vdc 1 L T1 1 Tl Tl 3n _ When ov + -^ 9--<9V +—' ^2 x L 4 „ z Tl Tl 71 71 71 _alt — U TT TT ( When 9v-- + - <o--<ev + - + -, ) Tl 71 71 371 Tl vV2_alt = *dc t t rx When 9v + - + ^<9--<9v + — + -. ^v2_alt = U ( When 9v-^-ti<9 - -<9v + --n. ) L -4- z. a ti ti 3n ^w2_alt ^dc When ev + - - n < e - - < ev + — - n . Y / XL ^w2_alt 0 / Tl Tl Tl 71 71 । When ev----<9--<9v + --~. LL l 71 71 71 3Tl Tl ^x2_alt ^dc When 9v + ---<9--<9v+—---~ Z L Z Z< ^x2_alt 0 . <h2 style=";text-align:left;direction:ltr"> <h2 style=";text-align:left;direction:ltr"> • ••(67)<h2 style=";text-align:left;direction:ltr"> The estimation unit 35 can then convert the four-phase applied voltage estimation values ​​of the first set Vul_alt, Vvl_alt, Vwl_alt, Vxl_alt into the d-axis and q-axis applied voltage estimation values ​​of the first set Vdl_alt, Vql_alt, by performing the well-known four-phase to two-phase conversion and rotation coordinate conversion based on the magnetic pole position 0 for the first set. The estimation unit 35 can convert the four-phase applied voltage estimation values ​​of the second set Vu2_alt, Vv2_alt, Vw2_alt, Vx2_alt into the d-axis and q-axis applied voltage estimation values ​​of the second set Vd2_alt, Vq2_alt, by performing the well-known four-phase to two-phase conversion and rotation coordinate conversion based on the magnetic pole position 0-ir / 4 for the second set.In the case of m phases, the well-known m-phase to two-phase conversion and rotation coordinate conversion are performed for the applied voltage estimation values ​​of m phases.

[0162]

[0160] <Estimation de courant de bus> The estimation unit 35 can estimate a bus current Idc flowing in the bus line which connects between the inverter of the first set 5a and the inverter of the second set 5b, and the DC power source 2.

[0163]

[0161] Similar to embodiment 1, the estimation unit 35 calculates the bus current Idc by the sum of products of the current detection values ​​of the armature windings and the estimation values ​​of applied voltages, and a product of the field current detection value if and the field voltage instruction value Vf, and dividing the sum by the DC voltage Vdc, as shown in equation (68) or equation (69). With the calculation according to this method, it is possible to calculate the bus current Idc with good accuracy by taking into account the influence of the third-order component of electrical angle. [Math. 68] 1 ^dc 77 C^ulKzl_a / t + + ^xl^xl_alt v dc ~^~^u2^u2_alt + ^v2^v2_alt "I” ^w2^w2_alt + ^x2^x2_alt + ' (^8) [Math. 69] 1 Idc 77 (JdlVdl_alt + IqlVql_alt + Id2^d2_alt Vdc + + ifVf ) ---(69)

[0164]

[0162] cInverter control unit 36> The inverter control unit 36 ​​converts the four-phase current detection values ​​of each set into the d-axis and q-axis current detection values ​​of each set by performing the well-known four-phase to two-phase conversion and rotation coordinate conversion according to the magnetic pole position for each set. Similar to Embodiment 1, the inverter control unit 36 ​​calculates the d-axis and q-axis voltage instruction values ​​of each set on the coordinate system of d-axis and q-axis rotation using equation (37), equation (38) and the like.

[0165]

[0163] Similar to embodiment 1, at the time of switching from alternator generation control to inverter control, the inverter control unit 36 ​​calculates the basic voltage instruction values ​​(in this example, the predictive voltage instruction values) of each set, based on the estimation values ​​of voltages applied when the inverter control

[0166]

[0167] alternator generation is performed.

[0164] For example, the inverter control unit 36 ​​sets the base voltage instruction values ​​to the applied voltage estimation values ​​at the time of switching and, after switching, gradually changes the base voltage instruction values ​​from the applied voltage estimation values ​​to the base voltage instruction values ​​set on the basis of the base voltage instruction values. current and electrical constants.

[0165] Similar to embodiment 1, after switching, using equation (39), the inverter control unit 36 ​​gradually changes the d-axis and q-axis predictive voltage instruction values ​​of each set from the d-axis and q-axis applied voltage estimation values ​​of each set to the d-axis and q-axis predictive voltage instruction values ​​of each set that are set on the basis of the current instruction values ​​and the electrical constants. Due to the similarity with embodiment 1, the explanation is

[0168] omitted.

[0166] <Autres modes de réalisation> (1) In the above-mentioned embodiment 1, the three-phase armature windings are provided for each set. However, provided that the number of phases of the armature winding is an odd number greater than or equal to three, it can be set to any odd number like five phases and seven phases.

[0169]

[0167] (2) In the above-mentioned embodiment 2, the four-phase armature windings are provided for each set. However, provided that the number of phases of the armature winding is an even number greater than or equal to three, it can be set to any even number like two phases and six phases.

[0170]

[0168] (3) In each of the aforementioned embodiments, the phase angles of the m-phase armature windings of the second set have been set on the phase-lagging side by ir / m / 2 or ir / m relative to the phase angles of the m-phase armature windings of the first set. However, the phase angles of the m-phase armature windings of the second set may be set on the phase-leading side by ir / m / 2 or n / m relative to the phase angles of the m-phase armature windings of the first set. The first set and the

[0171]

[0172]

[0173] second set can be replaced.

[0169] (4) In each of the aforementioned embodiments, the rotating electric machine 1 is used as a motor generator for the vehicle. However, the rotating electric machine 1 may be a motor generator for various types of devices. The rotating electric machine 1 may not operate as a motor, but can function as a generator.

[0170] (5) In each of the above-mentioned embodiments, the rotor is provided with the armature winding. However, the rotor may not be provided with the winding field, but be provided with a permanent magnet.

[0171] Although the present disclosure has been described above in terms of various exemplary embodiments and implementations, it should be understood that the various aspects, features, and functionalities described in several of the individual embodiments are not limited in their applicability to the particular embodiment with which they are described, but instead may be applied individually or in various combinations to one or more of the embodiments. It is therefore understood that many modifications that have not been exemplified may be made without departing from the scope of the present disclosure. For example, at least one of the constituent components may be modified, added, or eliminated. At least one of the constituent components recited in at least one of the preferred embodiments may be selected and combined with the constituent components mentioned in another preferred embodiment. List of reference signs

[0174]

[0172] 1: Rotating electric machine, 5a: First set inverter, 5b: Second set inverter, 30: Rotating electric machine control device, X: Phase angle difference, AOmin: Minimum phase angle difference

Claims

Claims

1. A rotating electric machine control device (30) which controls a rotating electric machine (1) having m-phase armature windings of a first set (m is an integer greater than or equal to 3) and m-phase armature windings of a second set, via a first set inverter (5a) and a second set inverter (5b) respectively, the rotating electric machine control device (30) executes alternator generation control which operates the inverter of each set as a rectifier by an induced voltage generated in the armature windings of each set by rotation of the rotating electric machine (1), and which operates the rotating electric machine (1) as a generator;and calculates estimation values ​​of applied voltages which are applied to the armature windings of each set, on the basis of detection values ​​of current flowing in the armature windings of each set when the alternator generation control is executed, wherein a minimum value of phase angle differences greater than 0 between a plurality of phase angles obtained by collecting a phase angle and a reverse phase angle of the armature winding of each phase in each set is set as a minimum phase angle difference (A0min) among phases of each set, and a phase angle difference of an electrical angle between the m-phase armature windings of the first set and the m-phase armature windings of the second set is equal to 1 / 2 of the minimum phase angle difference (A0min) among the phases of each set.;

2. A rotating electric machine control device (30) according to claim 1, wherein m is an odd number, the minimum phase angle difference (A0min) among the phases of each set is ir / m, and the phase angle difference between the m-phase armature windings of the first set and the m-phase armature windings of the second set is ir / m / 2.

3. A rotating electric machine control device (30) according to claim 2, calculates the estimation values ​​of applied voltages when the alternator generation control is executed, on the basis of a detection value of current ial flowing through the armature winding of phase Al among m phases of the first set, a detection value of current ib2 flowing through the armature winding of phase B2 among m phases of the second set, a phase angle difference of which with respect to phase Al is m / 2, and a detection value of current ic2 flowing through the armature winding of phase C2 among m phases of the second set, a phase angle difference of which with respect to phase Al is (jr-jr / m / 2).

4. A rotating electric machine control device (30) according to claim 3, calculates an amplitude of a first-order electrical angle component and an amplitude of a (2m-l)-th order electrical angle component which are included in the current detection value when the alternator generation control is executed, on the basis of the current detection value ial of phase A1, the current detection value ib2 of phase B2, and the current detection value ic2 of phase C2; ​​and calculates the estimation values ​​of applied voltages when the alternator generation control is executed, on the basis of the amplitude of the first-order electrical angle component and the amplitude of the (2m-l)-th order electrical angle component.

5. A rotary electric machine control device (30) according to claim 4, using a calculation equation of [Math. 1] _ îal ib2 ic2 lalA — 9 / n \ cos ~— \2mJ

6. calculates the first-order electrical angle component ial_l of the current detection value ial of phase Al, based on the current detection value ial of phase Al, the current detection value ib2 of phase B2, and the current detection value ic2 of phase C2; calculates the amplitude of the first-order electrical angle component, based on a value obtained by passing a square value of the first-order electrical angle component ial_l through a low-pass filter; using a calculation equation from [Math. 2] _ ^al ^b2 ^c2 ^al_2m —1 ~f 71 \ cos \2m) calculates the (2m-l)-th order electrical angle component ial_2m-l of the current detection value ial of phase Al, on the basis of the current detection value ial of phase Al, the current detection value ib2 of phase B2, and the current detection value ic2 of phase C2; ​​and calculates the magnitude of the (2m-l)-th order electrical angle component, on the basis of a value obtained by passing a square value of the (2m-l)-th order electrical angle component ial_2m-l through a low-pass filter. A rotating electric machine control device (30) according to claim 2, calculates the estimation values ​​of applied voltages when the alternator generation control is executed, on the basis of a detection value of current ial flowing through the armature winding of phase Al among m phases of the first set, a detection value of current ib2 flowing through the armature winding of phase B2 among m phases of the second set, a phase angle difference of which with respect to phase Al is m / 2, a detection value of current ic2 flowing through the armature winding of phase C2 among m phases of the second set, a phase angle difference of which with respect to phase Al is (jr-jr / m / 2), a detection value of current ia2 of phase A2 flowing through the armature winding of phase A2 among

7.

8. m phases of the second set, a phase angle difference of which with respect to phase A1 is ji / 2, a current detection value ibl of phase B1 among m phases of the first set, a phase angle difference of which with respect to phase A2 is m / 2, and a current detection value here of phase Cl among m phases of the first set, a phase angle difference of which with respect to phase A2 is (ir-jr / m / 2). The rotating electric machine control device (30) according to claim 6, calculates an amplitude of a first-order electrical angle component and an amplitude of a (2m-l)-th order electrical angle component which are included in the current detection value when the alternator generation control is executed, on the basis of the current detection value ial of phase A1, the current detection value ib2 of phase B2, the current detection value ic2 of phase C2, the current detection value ia2 of phase A2, the current detection value ibl of phase B1, the current detection value ici of phase C1; and calculates the estimation values ​​of applied voltages when the alternator generation control is executed, on the basis of the amplitude of the first-order electrical angle component and the amplitude of the (2m-l)-th order electrical angle component. A rotating electric machine control device (30) according to claim 7, using a calculation equation of [Math. 3] calculates the amplitude II of the first-order component of electrical angle, based on the current detection value ial of phase Al, the current detection value ib2 of phase B2, the current detection value ic2 of phase C2, the current detection value ia2 of phase A2, the detection value of current ibl of phase B1 and the current detection value here of phase Cl, using a calculation equation [Math. 4] 3 2 ^b2 — Îc2 calculates the amplitude I2m-1 of the (2m-l)-th order electrical angle component, based on the current detection value ial of phase Al, the current detection value ib2 of phase B2, the current detection value ic2 of phase C2, the current detection value ia2 of phase A2, the current detection value ibl of phase B1 and the current detection value ici of phase Cl.

9. A rotating electric machine control device (30) according to claim 6, calculates an amplitude and a phase angle of a first-order component of electrical angle and an amplitude and a phase angle of a (2m-l)-th order component of electrical angle which are included in the current detection value when the alternator generation control is executed, on the basis of the current detection value ial of phase A1, the current detection value ib2 of phase B2, the current detection value ic2 of phase C2, the current detection value ia2 of phase A2, the current detection value ibl of phase B1, the current detection value ici of phase C1;and calculates the estimation values ​​of applied voltages when the alternator generation control is executed, based on the amplitude and phase angle of the first-order component of electrical angle and the amplitude and phase angle of the (2m-l)-th-order component of electrical angle.;

10. A rotating electric machine control device (30) according to claim 9, using a calculation equation of [Math. 5] calculates the amplitude II and the phase angle A01 of the first-order component of electrical angle, based on the current detection value ial of phase Al, the current detection value ib2 of phase B2, the current detection value ic2 of phase C2, the current detection value ia2 of phase A2, the current detection value ibl of phase B1 and the current detection value ici of phase Cl, using a calculation equation of [Math. 6] 12m — 1 △^2m—1 calculates the amplitude I2m-1 and the phase angle 02m-1 of the (2m-l)-th order electrical angle component, based on the current detection value ial of phase Al, the current detection value ib2 of phase B2, the current detection value ic2 of phase C2, the current detection value ia2 of phase A2, the current detection value ibl of phase B1 and the current detection value ici of phase Cl.

11. A rotating electric machine control device (30) according to claim 1, wherein m is an even number, 67 the minimum phase angle difference (A0min) among the phases of each set is 2ir / m, and the phase angle difference between the m-phase armature windings of the first set and the m-phase armature windings of the second set is ir / m.

12. A rotating electric machine control device (30) according to claim 11, calculates the estimation values ​​of applied voltages when the alternator generation control is executed, on the basis of a current detection value ial flowing through the armature winding of phase Al among m phases of the first set, a current detection value ia2 flowing through the armature winding of phase A2 among m phases of the second set, a phase angle difference of which with respect to phase Al is m, and a current detection value ib2 flowing through the armature winding of phase B2 among m phases of the second set, a phase angle difference of which with respect to phase Al is (ir-ir / m).

13. A rotating electric machine control device (30) according to claim 12, calculates an amplitude of a first-order electrical angle component and an amplitude of a (ml)-th-order electrical angle component that are included in the current detection value when the alternator generation control is executed, on the basis of the current detection value ial of phase A1, the current detection value ia2 of phase A2, and the current detection value ib2 of phase B2; and calculates the estimation values ​​of applied voltages when the alternator generation control is executed, on the basis of the amplitude of the first-order electrical angle component and the amplitude of the (ml)-th-order electrical angle component.

14. A rotating electric machine control device (30) according to claim 13, using a calculation equation of [Math. 7] la2 “ lb2 COS — calculates the first-order electrical angle component ial_l of the current detection value ial of phase Al, based on the current detection value ial of phase Al, the current detection value ia2 of phase A2, and the current detection value ib2 of phase B2; calculates the amplitude of the first-order electrical angle component, based on a value obtained by passing a square value of the first-order electrical angle component ial_l through a low-pass filter; using a calculation equation [Math. 8] ^a2 lb2

15. cos — calculates the (ml)-th order electrical angle component ial_m-1 of the current detection value ial of phase Al, on the basis of the current detection value ial of phase Al, the current detection value ia2 of phase A2, and the current detection value ib2 of phase B2; and calculates the magnitude of the (ml)-th order electrical angle component, on the basis of a value obtained by passing a square value of the (ml)-th order electrical angle component ial_m-l through a low-pass filter. A rotating electric machine control device (30) according to claim 11, calculates the estimation values ​​of applied voltages when the alternator generation control is executed, on the basis of a detection value of current ial flowing through the armature winding of phase Al among m phases of the first set, a detection value of current ia2 flowing through the armature winding of phase A2 among m phases of the second set, a phase angle difference of which with respect to phase Al is jt /

16.

17. m, a current detection value ib2 flowing through the armature winding of phase B2 among m phases of the second set, a phase angle difference of which with respect to phase A1 is (jt-jt / m), a current detection value ibl of phase B1 flowing through the armature winding of phase B1 among m phases of the first set, a phase angle difference of which with respect to phase A1 is ji / 2, a current detection value ic2 flowing through the armature winding of phase C2 among m phases of the second set, a phase angle difference of which with respect to phase B1 is ir / m, and a current detection value id2 flowing through the armature winding of phase D2 among m phases of the second set, a phase angle difference of which with respect to phase B1 is (ir-ir / m).The rotating electric machine control device (30) according to claim 15, calculates the magnitude of the first-order electrical angle component and the magnitude of the (ml)-th-order electrical angle component which are included in the current detection value when the alternator generation control is executed, on the basis of the current detection value ial of phase A1, the current detection value ia2 of phase A2, the current detection value ib2 of phase B2, the current detection value ibl of phase B1, the current detection value ic2 of phase C2, and the current detection value id2 of phase D2; and calculates the estimation values ​​of applied voltages when the alternator generation control is executed, on the basis of the magnitude of the first-order electrical angle component and the magnitude of the (ml)-th-order electrical angle component. A rotary electric machine control device (30) according to claim 16, using a calculation equation [Math. 9] calculates the amplitude II of the first-order component of electrical angle, based on the current detection value ial of phase A1, the current detection value ia2 of phase A2, the current detection value ib2 of phase B2, the current detection value ibl of phase B1, the current detection value ic2 of phase C2 and the current detection value id2 of phase D2; and using a calculation equation from [Math. 10] Îa2 î-b2 ^c2 ^d2

18. calculates the amplitude Im-1 of the (ml)-th order component of electrical angle, based on the current detection value ial of phase Al, the current detection value ia2 of phase A2, the current detection value ib2 of phase B2, the current detection value ibl of phase B1, the current detection value ic2 of phase C2 and the current detection value id2 of phase D2. The rotating electric machine control device (30) according to claim 15, calculates an amplitude and a phase angle of a first-order component of electrical angle and an amplitude and a phase angle of a (ml)-th-order component of electrical angle which are included in the current detection value when the alternator generation control is executed, on the basis of the current detection value ial of phase A1, the current detection value ia2 of phase A2, the current detection value ib2 of phase B2, the current detection value ibl of phase B1, the current detection value ic2 of phase C2, the current detection value id2 of phase D2;and calculates the estimation values ​​of applied voltages when the alternator generation control is executed, based on the amplitude and phase angle of the first-order component of electrical angle and the amplitude and phase angle of the (ml)-th-order component of electrical angle.;

19. A rotating electric machine control device (30) according to claim 18, using a calculation equation of [Math. 11] calculates the amplitude II and the phase angle A01 of the first-order component of electrical angle, based on the current detection value ial of phase A1, the current detection value ia2 of phase A2, the current detection value ib2 of phase B2, the current detection value ibl of phase B1, the current detection value ic2 of phase C2 and the current detection value id2 of phase D2; using a calculation equation from [Math. 12] calculates the amplitude Im-1 and the phase angle A0m-1 of the (ml)-th order component of electrical angle, based on the current detection value ial of phase Al, the current detection value ia2 of phase A2, the current detection value ib2 of phase B2, the current detection value ibl of phase B1, current detection value ic2 of phase C2 and current detection value id2 of phase D2.

20. A rotating electric machine control device (30) according to claim 1, switches and executes inverter control and alternator generation control; wherein, the inverter control is configured to calculate basic voltage command values, based on armature winding current command values ​​and electrical constants of the rotating electric machine (1), for each set; calculate voltage command values, based on the basic voltage command values, for each set; and turn on and off a plurality of inverter switching devices of each set, and apply voltage to the m-phase armature windings of each set, based on the voltage command values ​​of each set;when switching from alternator generation control to inverter control, calculates the base voltage instruction values ​​of each set, based on the estimation values ​​of voltages applied when the alternator generation control is executed.;

21. A rotating electric machine control device (30) according to claim 1, when the alternator generation control is executed, calculates an estimation value of a bus current flowing in a bus line that connects the first set inverter (5a) and the second set inverter (5b) to a DC power source, on the basis of the detection values ​​of current flowing in the armature windings of each set, and the estimation values ​​of voltages applied when the alternator generation control is executed.

22. A rotating electric machine control device (30) according to any one of claims 1 to 21, wherein the rotating electric machine (1) is a motor generator for a vehicle.

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