Antenna device and wireless device

Abstract

To provide an antenna device and a wireless device capable of improving characteristics.SOLUTION: According to an embodiment, an antenna device includes a waveguide including a feed point and a first region. The first region is located around the feeding point in a first plane intersecting a first axial direction passing through the feeding point. The waveguide includes a plurality of radiating parts provided in the first region. Each of the plurality of radiating parts includes a first slot along a first slot direction and a second slot along a second slot direction. The plurality of radiating parts include a first radiating part and a second radiating part. A first radiating part direction from the feeding point to the first radiating part intersects the first axial direction. A second radiating part direction from the feeding point to the second radiating part intersects the first axial direction and the first radiating part direction. A second absolute value of a second angular difference between the first slot direction in the second radiating part and the second radiating part direction is less than a first absolute value of a first angular difference between the first slot direction in the first radiating part and the first radiating part direction.SELECTED DRAWING: Figure 1

Description

[Technical Field]

[0001] FIELD An embodiment of the present invention relates to an antenna device and a wireless device. [Background technology]

[0002] For example, improved characteristics are desired in antenna devices and wireless devices. [Prior art documents] [Patent documents]

[0003] [Patent Document 1] Japanese Patent Application Publication No. 5-129831 Summary of the Invention [Problem to be solved by the invention]

[0004] The embodiments of the present invention provide an antenna device and a radio device that can improve characteristics. [Means for solving the problem]

[0005] According to an embodiment of the present invention, an antenna device includes a waveguide including a feed point and a first region. The first region is located around the feed point on a first plane intersecting a first axis direction passing through the feed point. The waveguide includes a plurality of radiating portions provided in the first region. Each of the plurality of radiating portions includes a first slot extending along a first slot direction and a second slot extending along a second slot direction intersecting the first slot direction. The plurality of radiating portions include a first radiating portion and a second radiating portion. A first radiating portion direction from the feed point to the first radiating portion intersects the first axis direction. A second radiating portion direction from the feed point to the second radiating portion intersects the first axis direction and intersects the first radiating portion direction. A second absolute value of a second angular difference between the first slot direction and the second radiating portion direction in the second radiating portion is smaller than a first absolute value of a first angular difference between the first slot direction and the first radiating portion direction in the first radiating portion. [Brief explanation of the drawings]

[0006] [Figure 1] 1(a) and 1(b) are schematic views illustrating an antenna device according to a first embodiment. [Figure 2] FIG. 2 is a schematic plan view illustrating the antenna device according to the first embodiment. [Figure 3] FIG. 3 is a schematic plan view illustrating a part of the antenna device according to the first embodiment. [Figure 4] FIG. 4 is a schematic diagram illustrating the antenna device according to the first embodiment. [Figure 5] 5(a) and 5(b) are graphs illustrating the antenna device according to the first embodiment. [Figure 6] 6(a) and 6(b) are graphs illustrating the antenna device according to the first embodiment. [Figure 7] 7(a) to 7(c) are schematic cross-sectional views illustrating the antenna device according to the first embodiment. [Figure 8] 8(a) and 8(b) are schematic perspective views illustrating a part of the antenna device according to the first embodiment. [Figure 9] FIG. 9 is a schematic perspective view illustrating the antenna device according to the first embodiment. [Figure 10] FIG. 10 is a schematic plan view illustrating the antenna device according to the first embodiment. [Figure 11] FIG. 11 is a graph illustrating the characteristics of the antenna device. [Figure 12] FIG. 12 is a graph illustrating the characteristics of the antenna device according to the first embodiment. [Figure 13] FIG. 13 is a graph illustrating the characteristics of the antenna device according to the first embodiment. [Figure 14] FIG. 14 is a graph illustrating the characteristics of the antenna device according to the first embodiment. [Figure 15] FIG. 15 is a graph illustrating the characteristics of the antenna device according to the first embodiment. [Figure 16] 16(a) and 16(b) are schematic plan views illustrating the characteristics of the antenna device. [Figure 17] FIG. 17 is a schematic plan view illustrating a part of the antenna device according to the first embodiment. [Figure 18] 18(a) and 18(b) are graphs illustrating the characteristics of the antenna device according to the embodiment. [Figure 19] FIG. 19 is a graph illustrating the antenna device according to the first embodiment. [Figure 20] FIG. 20 is a schematic plan view illustrating a part of the antenna device according to the first embodiment. [Figure 21] 21(a) and 21(b) are schematic views illustrating the antenna device according to the first embodiment. [Figure 22] 22(a) and 22(b) are schematic views illustrating the antenna device according to the first embodiment. [Figure 23] FIG. 23 is a graph illustrating the antenna device according to the first embodiment. [Figure 24] FIG. 24 is a graph illustrating the antenna device according to the first embodiment. [Figure 25] 25(a) and 25(b) are schematic plan views illustrating the antenna device. [Figure 26] FIG. 26 is a graph illustrating the characteristics of the antenna device. [Figure 27] FIG. 27 is a graph illustrating the characteristics of the antenna device. [Figure 28] 28(a) and 28(b) are graphs illustrating the characteristics of the antenna device. [Figure 29] FIG. 29 is a schematic cross-sectional view illustrating the antenna device according to the second embodiment. [Figure 30] FIG. 30 is a schematic perspective view illustrating the antenna device according to the second embodiment. [Figure 31] FIG. 31 is a schematic perspective view illustrating the antenna device according to the second embodiment. [Figure 32]FIG. 32 is a schematic diagram illustrating a part of the antenna device according to the second embodiment. [Figure 33] FIG. 33 is a schematic diagram illustrating the antenna device according to the second embodiment. [Figure 34] FIG. 34 is a schematic diagram illustrating the antenna device according to the second embodiment. [Figure 35] FIG. 35 is a schematic diagram illustrating the antenna device according to the second embodiment. [Figure 36] 36(a) and 36(b) are schematic diagrams illustrating the characteristics of the antenna device according to the second embodiment. [Figure 37] FIG. 37 is a schematic perspective view illustrating the antenna device according to the second embodiment. [Figure 38] FIG. 38 is a schematic diagram illustrating a wireless device according to the third embodiment. DETAILED DESCRIPTION OF THE INVENTION

[0007] Hereinafter, an embodiment of the present invention will be described with reference to the drawings. The drawings are schematic or conceptual, and the relationship between the thickness and width of each part, the size ratio between parts, etc. are not necessarily the same as those in reality. Even when the same part is shown, the dimensions and ratios may be different depending on the drawing. In this specification and in each drawing, elements similar to those previously described with reference to the previous drawings are designated by the same reference numerals, and detailed descriptions thereof will be omitted where appropriate.

[0008] (First embodiment) 1(a) and 1(b) are schematic views illustrating an antenna device according to a first embodiment. Fig. 1(a) is a plan view, and Fig. 1(b) is a cross-sectional view taken along line A1-A2 in Fig. 1(a). FIG. 2 is a schematic plan view illustrating the antenna device according to the first embodiment. FIG. 3 is a schematic plan view illustrating a part of the antenna device according to the first embodiment. FIG. 4 is a schematic diagram illustrating the antenna device according to the first embodiment.

[0009] As shown in FIGS. 1(a) and 1(b), an antenna device 110 according to the embodiment includes a waveguide 10w. The waveguide 10w includes a feed point 10c and a first region 10r. The first region 10r is planar. For example, the first region 10r is located around the feed point 10c on a first plane PL1 that intersects with a first axis direction Dz1 that passes through the feed point 10c. For example, the first region 10r is annular with the feed point 10c as its center.

[0010] The first axis direction Dz1 is defined as the Z-axis direction. A direction perpendicular to the Z-axis direction is defined as the X-axis direction. A direction perpendicular to the Z-axis direction and the X-axis direction is defined as the Y-axis direction. In one example, the first surface PL1 is aligned along the XY plane.

[0011] The waveguide 10w includes a plurality of radiating portions 20 provided in the first region 10r. For example, as shown in FIG. 1(b), the waveguide 10w may include a first conductive layer 41. The first conductive layer 41 is along the first plane PL1. The first conductive layer 41 includes a plurality of openings 45. The plurality of openings 45 correspond to the plurality of radiating portions 20. As shown in FIG. 1(b), the waveguide 10w may include a second conductive layer 42. The direction from the second conductive layer 42 to the first conductive layer 41 is along the Z-axis direction. A first member 30 may be provided between the second conductive layer 42 and the first conductive layer 41. The first member 30 includes, for example, a dielectric material.

[0012] In one example, a high-frequency signal is input to a feed point 10c of the waveguide 10w via a coaxial line 25 (see FIG. 1(b)). For example, the coaxial line 25 includes an inner conductor 25i and an outer conductor 25o surrounding the inner conductor 25i. The feed point 10c overlaps with an end of the inner conductor 25i (signal line) in the Z-axis direction. The waveguide 10w is configured to guide the high-frequency signal supplied to the feed point 10c. The high-frequency signal supplied to the feed point 10c is radiated from multiple radiating portions 20.

[0013] 1(a), each of the multiple radiating sections 20 includes a first slot 21 and a second slot 22. The first slot 21 and the second slot 22 are included in one slot pair. The first slot 21 corresponds to one of the multiple openings 45. The second slot 22 corresponds to another of the multiple openings 45.

[0014] 3 illustrates one of the multiple radiating sections 20 (one slot pair 20p). The first slot 21 extends along a first slot direction Ds1. The second slot 22 extends along a second slot direction Ds2. The second slot direction Ds2 intersects with the first slot direction Ds1. The second slot direction Ds2 may be substantially perpendicular to the first slot direction Ds1.

[0015] As shown in FIG. 2, the angle in the circumferential direction is defined as the azimuth angle φ. The circumferential direction is centered at the feed point 10c and extends along the first plane PL1. The direction passing through the feed point 10c and extending along the first plane PL1 is defined as the radial direction ρ. The feed point 10c corresponds to the origin OP of the coordinate system. In the following example, the azimuth angle φ is set to 0 in the positive X-axis direction.

[0016] 1(a), the plurality of radiating portions 20 include a first radiating portion 20a and a second radiating portion 20b. As will be described later, the plurality of radiating portions 20 may further include a third radiating portion 20c. The plurality of radiating portions 20 may further include a fourth radiating portion 20d.

[0017] As shown in FIG. 4, a first radiating portion direction Dp1 from the feed point 10c to the first radiating portion 20a intersects with the first axis direction Dz1. A second radiating portion direction Dp2 from the feed point 10c to the second radiating portion 20b intersects with the first axis direction Dz1 and the first radiating portion direction Dp1. The second radiating portion direction Dp2 may be substantially perpendicular to the first radiating portion direction Dp1. In the example of FIG. 4, the first radiating portion direction Dp1 corresponds to the positive X-axis direction. In the example of FIG. 4, the second radiating portion direction Dp2 corresponds to the positive Y-axis direction. In the example of FIG. 4, the azimuth angle φ is 0° in the first radiating portion 20a. The azimuth angle φ is 90° in the second radiating portion 20b.

[0018] As shown in Fig. 4, the angular difference between the first slot direction Ds1 of the first radiating portion 20a and the first radiating portion direction Dp1 is defined as a first angular difference β1. The angular difference between the first slot direction Ds1 of the second radiating portion 20b and the second radiating portion direction Dp2 is defined as a second angular difference β2. In the embodiment, the second absolute value of the second angular difference β2 is smaller than the first absolute value of the first angular difference β1. This configuration makes it possible to provide an antenna device capable of improving characteristics.

[0019] For example, an antenna device may be used to transmit and receive electromagnetic waves in a direction tilted with respect to the Z-axis direction. In the characteristics of an antenna device for such an application, anisotropy is provided on the first surface PL1. For example, the configuration of the first member 30 at a position where the azimuth angle φ is 0° differs from the configuration of the first member 30 at a position where the azimuth angle φ is different from 0°. This allows electromagnetic waves to be transmitted and received in a tilted direction. In the embodiment, the above-described angle difference configuration allows, for example, electromagnetic waves to be efficiently transmitted and received in a tilted direction while maintaining high waveguiding characteristics.

[0020] For example, when transmitting and receiving electromagnetic waves in a tilted direction, the equiphase surface becomes a flattened circle (for example, an ellipse). In the embodiment, the angle difference configuration as described above can maintain, for example, high waveguiding characteristics.

[0021] In the first reference example, the second absolute value of the second angular difference β2 is the same as the first absolute value of the first angular difference β1. In the first reference example, the directions of the multiple radiating sections 20 are rotated in conjunction with (proportional to) the azimuth angle φ. In such a first reference example, differences in characteristics occur among the multiple radiating sections 20. For example, the characteristics of the first slot 21 and the characteristics of the second slot 22 become non-uniform among the multiple radiating sections 20. In the first reference example, the band becomes narrower and the polarization characteristics deteriorate.

[0022] In contrast, in the embodiment, the second absolute value of the second angle difference β2 is smaller than the first absolute value of the first angle difference β1. For example, in the second radiating portion 20b at a position where the azimuth angle φ is 90°, the rotation angle of the second radiating portion 20b is smaller than 90°. This reduces the difference in characteristics among the multiple radiating portions 20. For example, non-uniformity between the characteristics of the first slot 21 and the characteristics of the second slot 22 among the multiple radiating portions 20 is suppressed. According to the embodiment, for example, a wide bandwidth can be maintained. For example, deterioration of the polarization characteristics can be suppressed. Examples of the characteristics of the antenna device 110 will be described later.

[0023] 4, the multiple radiating portions 20 may further include a third radiating portion 20c. A third radiating portion direction Dp3 from the feed point 10c to the third radiating portion 20c intersects the first axis direction Dz1 and the second radiating portion direction Dp2. The feed point 10c is located between the third radiating portion 20c and the first radiating portion 20a in the direction along the first radiating portion direction Dp1. The feed point 10c is located between the third radiating portion 20c and the first radiating portion 20a in the direction along the third radiating portion direction Dp3.

[0024] As shown in Fig. 4, the multiple radiating portions 20 may further include a fourth radiating portion 20d. A fourth radiating portion direction Dp4 from the feed point 10c to the fourth radiating portion 20d intersects the first axis direction Dz1 and the first radiating portion direction Dp1. The feed point 10c is located between the fourth radiating portion 20d and the second radiating portion 20b in the direction along the second radiating portion direction Dp2. The feed point 10c is located between the fourth radiating portion 20d and the second radiating portion 20b in the direction along the fourth radiating portion direction Dp4.

[0025] The angular difference between the first slot direction Ds1 and the radiating portion direction in each of the multiple radiating portions 20 is defined as an angular difference β0.

[0026] 5(a) and 5(b) are graphs illustrating the antenna device according to the first embodiment. The horizontal axis in these figures is the azimuth angle φ. The vertical axis in Fig. 5(a) is the angle difference β0. In Fig. 5(a), an azimuth angle φ of 0° corresponds to the first radiating portion 20a. An azimuth angle φ of 90° corresponds to the second radiating portion 20b. An azimuth angle φ of 180° corresponds to the third radiating portion 20c. An azimuth angle φ of 270° corresponds to the fourth radiating portion 20d.

[0027] As shown in FIG. 5A, in the antenna device 110 according to this embodiment, the second absolute value of the second angular difference β2 corresponding to the second radiating portion 20b is smaller than the first absolute value of the first angular difference β1 corresponding to the first radiating portion 20a. The third absolute value of the third angular difference β3 corresponding to the third radiating portion 20c is larger than the second absolute value of the second angular difference β2. The third angular difference β3 may be substantially the same as the first angular difference β1. The fourth absolute value of the fourth angular difference β4 corresponding to the fourth radiating portion 20d is larger than the first absolute value of the first angular difference β1. The fourth absolute value of the fourth angular difference β4 is larger than the third absolute value of the third angular difference β3.

[0028] As shown in FIG. 5(a), in the first reference example 119 (broken line) described above, even if the azimuth angle φ changes, the angular difference β0 remains constant.

[0029] In the antenna device 110, when the azimuth angle φ of the radiating portion 20 is located between the azimuth angle φ of the first radiating portion 20a and the azimuth angle φ of the second radiating portion 20b, the angle difference β0 may be between the first angle difference β1 and the second angle difference β2. When the azimuth angle φ of the radiating portion 20 is located between the azimuth angle φ of the second radiating portion 20b and the azimuth angle φ of the third radiating portion 20c, the angle difference β0 may be between the second angle difference β2 and the third angle difference β3. When the azimuth angle φ of the radiating portion 20 is located between the azimuth angle φ of the third radiating portion 20c and the azimuth angle φ of the fourth radiating portion 20d, the angle difference β0 may be between the third angle difference β3 and the fourth angle difference β4. In the radiating portion 20 where the azimuth angle φ is between the azimuth angle φ of the fourth radiating portion 20d and the azimuth angle φ of the first radiating portion 20a, the angle difference β0 may be between the fourth angle difference β4 and the first angle difference β1.

[0030] As shown in Fig. 4, the angular difference between the second slot direction Ds2 of the first radiating portion 20a and the first radiating portion direction Dp1 is defined as a first angular difference γ1. The angular difference between the second slot direction Ds2 of the second radiating portion 20b and the second radiating portion direction Dp2 is defined as a second angular difference γ2. The angular difference between the second slot direction Ds2 of the third radiating portion 20c and the third radiating portion direction Dp3 is defined as a third angular difference γ3. The angular difference between the second slot direction Ds2 of the fourth radiating portion 20d and the fourth radiating portion direction Dp4 is defined as a fourth angular difference γ4.

[0031] The angular difference between the second slot direction Ds2 and the radiating portion direction in each of the plurality of radiating portions 20 is defined as another angular difference γ0.

[0032] The vertical axis of Fig. 5(b) is the angular difference γ0. In Fig. 5(b), an azimuth angle φ of 0° corresponds to the first radiating portion 20a. An azimuth angle φ of 90° corresponds to the second radiating portion 20b. An azimuth angle φ of 180° corresponds to the third radiating portion 20c. An azimuth angle φ of 270° corresponds to the fourth radiating portion 20d.

[0033] As shown in FIG. 5(b), the second other angular difference γ2 in the second radiating portion 20b is larger than the first other angular difference γ1 corresponding to the first radiating portion 20a. The third other angular difference γ3 in the third radiating portion 20c is smaller than the second other angular difference γ2. The third other angular difference γ3 may be substantially the same as the first other angular difference γ1. The fourth other angular difference γ4 in the fourth radiating portion 20d is smaller than the first other angular difference γ1. The fourth other angular difference γ4 is smaller than the third other angular difference γ3.

[0034] In the antenna device 110, when the azimuth angle φ of the radiating portion 20 is located between the azimuth angle φ of the first radiating portion 20a and the azimuth angle φ of the second radiating portion 20b, the other angular difference γ0 may be between the first other angular difference γ1 and the second other angular difference γ2. When the azimuth angle φ of the radiating portion 20 is located between the azimuth angle φ of the second radiating portion 20b and the azimuth angle φ of the third radiating portion 20c, the other angular difference γ0 may be between the second other angular difference γ2 and the third other angular difference γ3. When the azimuth angle φ of the radiating portion 20 is located between the azimuth angle φ of the third radiating portion 20c and the azimuth angle φ of the fourth radiating portion 20d, the other angular difference γ0 may be between the third other angular difference γ3 and the fourth other angular difference γ4. In a radiating section 20 where the azimuth angle φ is located between the azimuth angle φ of the fourth radiating section 20d and the azimuth angle φ of the first radiating section 20a, the other angular difference γ0 may be between the fourth other angular difference γ4 and the first other angular difference γ1.

[0035] In the embodiment, for example, the sum of the angle difference β0 and the other angle difference γ0 may be substantially 90°. For example, the sum of the first angle difference β1 and the first other angle difference γ1 may be 80° or more and 100° or less. For example, the sum of the second angle difference β2 and the second other angle difference γ2 may be 80° or more and 100° or less. For example, the sum of the third angle difference β3 and the third other angle difference γ3 may be 80° or more and 100° or less. For example, the sum of the fourth angle difference β4 and the fourth other angle difference γ4 may be 80° or more and 100° or less.

[0036] 6(a) and 6(b) are graphs illustrating the antenna device according to the first embodiment. The horizontal axis in these figures is the azimuth angle φ. The vertical axis in FIG. 6(a) is the angular difference β0. As shown in FIG. 6(a), the first angular difference β1 and the third angular difference β3 may each be substantially 45°. The second angular difference β2 may be approximately 30°. The fourth angular difference β4 may be approximately 60°.

[0037] 6(b), the first other angular difference γ1 and the third other angular difference γ3 may each be substantially 45°, the second other angular difference γ2 may be approximately 30°, and the fourth other angular difference γ4 may be approximately 30°.

[0038] As shown in FIG. 1(a), in the embodiment, the first region 10r may include a first partial region 11 and a second partial region 12. The feed point 10c is located between the second partial region 12 and the first partial region 11 in a first intersecting direction Dx1 that intersects with the first axis direction Dz1. The first intersecting direction Dx1 may be, for example, the X-axis direction. For example, the waveguiding characteristics in the first partial region 11 are different from the waveguiding characteristics in the second partial region 12. As a result, the electromagnetic wave is emitted in a direction inclined with respect to the Z-axis direction.

[0039] In the embodiment, for example, the waveguide 10w includes a first member 30. As shown in FIG. 1(b), the first member 30 includes a first member region 31 and a second member region 32. The first member region 31 corresponds to the first partial region 11. The second member region 32 corresponds to the second partial region 12. The first member region 31 and the second member region 32 may satisfy at least one of a first condition, a second condition, a third condition, a fourth condition, and a fifth condition.

[0040] Under the first condition, the first relative dielectric constant of the first component region 31 is different from the second relative dielectric constant of the second component region 32. Under the second condition, the density of the plurality of first holes 31h included in the first component region 31 is different from the density of the plurality of second holes 32h included in the second component region 32 (see FIG. 1(b)).

[0041] In the third condition, a first average size of the plurality of first holes 31h included in the first component region 31 is different from a second average size of the plurality of second holes 32h included in the second component region 32. In the fourth condition, a first configuration of the first structures provided in the first component region 31 is different from a second configuration of the second structures provided in the second component region 32. The first configuration and the second configuration may include, for example, surface irregularities.

[0042] In the fifth condition, the thickness of the first member 30 included in the first member region 31 is different from the thickness of the first member 30 included in the second member region 32. The thickness is the length along the first axis direction Dz1. A slow-wave structure may be provided based on such first to fifth conditions. The slow-wave structure makes it possible to transmit and receive electromagnetic waves in a tilted direction. In the embodiment, for example, even when such first to fifth conditions are applied, it is possible to improve the characteristics.

[0043] As shown in FIG. 3 , the length of the first slot 21 along the first slot direction Ds1 is defined as the first slot length L1. The length of the first slot 21 along the direction perpendicular to the first slot direction Ds1 is defined as the first slot width W1. The first slot length L1 is longer than the first slot width W1. For example, the first slot length L1 may be 1.5 times or more the first slot width W1. The length of the second slot 22 along the second slot direction Ds2 is defined as the second slot length L2. The length of the second slot 22 along the direction perpendicular to the second slot direction Ds2 is defined as the second slot width W2. The second slot length L2 is longer than the second slot width W2. For example, the second slot length L2 may be 1.5 times or more the second slot width W2.

[0044] For example, the first slot 21 included in the first radiating section 20a has a first slot length L1 along the first slot direction Ds1. The second slot 22 included in the first radiating section 20a has a second slot length L2 along the second slot direction Ds2. The ratio of the absolute value of the difference between the first slot length L1 and the second slot length L2 to the first slot length L1 may be 0.1 or less. For example, the second slot length L2 may be substantially the same as the first slot length L1. The second slot width W2 may be substantially the same as the first slot width W1.

[0045] As shown in FIG. 3 , in one of the multiple radiating units 20 (one slot pair 20p), the angle between one direction (e.g., the X-axis direction) and the first slot direction Ds1 is defined as a first slot angle δ1. In one of the multiple radiating units 20 (one slot pair 20p), the angle between the one direction (e.g., the X-axis direction) and the second slot direction Ds2 is defined as a second slot angle δ2. For example, the ratio of the difference between the absolute value of the first slot angle δ1 and the absolute value of the second slot angle δ2 to the absolute value of the first slot angle δ1 may be 0.1 or less. For example, the absolute value of the second slot angle δ2 may be substantially the same as the absolute value of the first slot angle δ1. For example, the angle between the first slot direction Ds1 and the second slot direction Ds2 may be 80° or more and 100° or less (e.g., substantially 90°).

[0046] In an embodiment, a high-frequency signal may be supplied to the feed point 10c via, for example, a waveguide, etc. A high-frequency signal may be supplied to the feed point 10c by, for example, electromagnetic coupling from another circuit not included in the antenna device.

[0047] 7(a) to 7(c) are schematic cross-sectional views illustrating the antenna device according to the first embodiment. As shown in FIG. 7(a), in an antenna device 110a according to this embodiment, the outer conductor 25o of the coaxial line 25 is electrically connected to the second conductive layer 42 of the waveguide 10w. The inner conductor 25i of the coaxial line 25 is inserted into the waveguide 10w. For example, impedance matching can be achieved by changing the insertion length of the inner conductor 25i. To insert the inner conductor 25i, a hole having a diameter similar to that of the inner conductor 25i may be provided in the first member 30.

[0048] 7(b), in the antenna device 110b according to the embodiment, the first member 30 is not provided locally in a part of the periphery of the inner conductor 25i. For example, impedance matching can be achieved by controlling the length (size) of the region where the first member 30 is not provided.

[0049] As shown in Fig. 7(c), in an antenna device 110c according to this embodiment, the shape of the end of the inner conductor 25i is different from that in the antenna device 110b, and impedance matching is achieved.

[0050] 8(a) and 8(b) are schematic perspective views illustrating a part of the antenna device according to the first embodiment. These figures illustrate a part of the waveguide 10w. As shown in FIG. 8(a), in the antenna device 110d according to this embodiment, the first member 30 includes a dielectric 38. For example, the guided wavelength in the waveguide 10w changes depending on the relative dielectric constant of the dielectric 38. If the relative dielectric constant is ε r The wavelength in free space is λ0. The guided wavelength of the waveguide 10w is λ g is λ g =λ0 / (ε r ) 1 / 2 It is expressed as:

[0051] When the waveguide 10w is a waveguide, the guided wavelength also changes depending on the tube width of the waveguide. In addition to the relative dielectric constant, the tube width may be changed, thereby adjusting the guided wavelength. Even when the relative dielectric constant of the dielectric 38 is substantially 1, the first member 30 may be considered to be a slow-wave structure.

[0052] As shown in FIG. 8(b), in an antenna device 110e according to the embodiment, a dielectric 38 is provided in a portion of the waveguide 10w. As in the example of FIG. 8(b), a gap may be provided between at least a portion of the dielectric 38 and the first conductive layer 41. When the dielectric 38 is provided partially, the guided wavelength is controlled by controlling the filling rate of the dielectric 38. For example, the partially filled dielectric 38 may be in contact with the first conductive layer 41. The partially filled dielectric 38 may be in contact with the second conductive layer 42.

[0053] Dielectric 38 may include multiple different dielectric portions with different structures or compositions. For example, dielectric 38 may include multiple dielectric portions with different dielectric constants. The fill factor of one of the multiple dielectric portions may be different from the fill factor of another of the multiple dielectric portions. The material of one of the multiple dielectric portions may be the same as the material of another of the multiple dielectric portions.

[0054] The first member 30 may include, for example, a metamaterial. In a metamaterial, structures including, for example, a dielectric or a metal are periodically arranged. When the first member 30 includes a metamaterial, the slow wave ratio of the waveguide 10w may partially be a value greater than or equal to 1, or may be a negative value.

[0055] The density of the dielectric 38 may be changed to change the effective dielectric constant. By changing the density of the dielectric 38, for example, it is possible to control the distribution of the dielectric constant using one type of dielectric 38. For example, it is possible to change the density of the dielectric 38 by providing holes in the dielectric 38. For example, the dielectric 38 may be printed using a 3D printer while changing the filling rate of the dielectric 38. This allows the density of the dielectric 38 to be changed.

[0056] The thickness of the dielectric 38 may be changed to change the effective dielectric constant. By changing the thickness of the dielectric 38, for example, it is possible to control the distribution of the dielectric constant while using one type of dielectric 38. The thickness of the dielectric 38 may be changed substantially continuously. The thickness of the dielectric 38 may be changed substantially discretely. For example, the thickness of the dielectric 38 may be changed continuously by cutting the dielectric 38. For example, the thickness of the dielectric 38 may be changed discretely by printing the dielectric 38 with a 3D printer.

[0057] For example, with this configuration, at least one of the above first to fifth conditions may be provided. The guided wavelength can be easily controlled with this first member 30. A wide control range of the guided wavelength can be obtained.

[0058] For example, with the above configuration, electromagnetic waves are transmitted and received along a direction inclined (tilted) with respect to the Z-axis direction, based on the anisotropy of the guided wavelength within the first surface PL1, for example.

[0059] As already described, the first region 10r includes the first partial region 11 and the second partial region 12 (see FIG. 1(a)). The feed point 10c is located between the first partial region 11 and the second partial region 12 in the first intersecting direction Dx1 that intersects with the first axis direction Dz1. The first guided wavelength λ1 in the waveguide 10w in the first partial region 11 is different from the second guided wavelength λ2 in the waveguide 10w in the second partial region 12. For example, the first guided wavelength λ1 is shorter than the second guided wavelength λ2.

[0060] The first guided wavelength λ1 is the wavelength of the high-frequency signal propagating in the direction from the feed point 10c to the first subregion 11. The second guided wavelength λ2 is the wavelength of the high-frequency signal propagating in the direction from the feed point 10c to the second subregion 12.

[0061] When the first guided wavelength λ1 is shorter than the second guided wavelength λ2, the radiated electromagnetic wave tilts in a direction inclined from the first axis direction Dz1 toward the first partial region 11. For example, the projection direction of the main radiation direction of the electromagnetic wave onto the waveguide 10w is along the direction from the second partial region 12 to the first partial region 11.

[0062] When the waveguide 10w includes the first member 30, a first slow wave factor in the first partial region 11 of the first member 30 is different from a second slow wave factor in the second partial region 12 of the first member 30. For example, the first slow wave factor is lower than the second slow wave factor. For example, the effective relative dielectric constant in the first partial region 11 is higher than the effective relative dielectric constant in the second partial region 12. For example, the relative dielectric constant in the first partial region 11 may be higher than the relative dielectric constant in the second partial region 12.

[0063] As shown in FIG. 1( a), the first region 10r may include a third partial region 13 and a fourth partial region 14. The feed point 10c is located between the third partial region 13 and the fourth partial region 14. The direction from the feed point 10c to the third partial region 13 intersects with the direction from the feed point 10c to the first partial region 11. The direction from the feed point 10c to the fourth partial region 14 intersects with the direction from the feed point 10c to the first partial region 11. An angle between the direction from the feed point 10c to the third partial region 13 and the direction from the feed point 10c to the first partial region 11 may be substantially 90°. An angle between the direction from the feed point 10c to the fourth partial region 14 and the direction from the feed point 10c to the first partial region 11 may be substantially 90°.

[0064] For example, the third guided wavelength λ3 in the waveguide in the third sub-region 13 is longer than the first guided wavelength λ1 and shorter than the second guided wavelength λ2. The fourth guided wavelength λ4 in the waveguide in the fourth sub-region 14 is longer than the first guided wavelength λ1 and shorter than the second guided wavelength λ2. For example, a high degree of design freedom can be maintained in the third sub-region 13 and the fourth sub-region 14. The antenna performance can be improved. For example, the effective dielectric constant in the third sub-region 13 may be between the effective dielectric constant in the first sub-region 11 and the effective dielectric constant in the second sub-region 12. For example, the effective dielectric constant in the fourth sub-region 14 may be between the effective dielectric constant in the first sub-region 11 and the effective dielectric constant in the second sub-region 12.

[0065] For example, a radial line slot antenna includes a waveguide and a plurality of slots. The waveguide is a radial waveguide. The radial waveguide is substantially circular. The plurality of slots function as radiating elements. The plurality of slots are arranged in a spiral or concentric pattern.

[0066] Generally, in a radial line slot antenna, the slot pairs are rotated at an angle proportional to the circumferential angle (azimuth angle φ) of the line connecting the feed point and the multiple slot pairs. In a radial waveguide in which the retardation rate in the waveguide is uniform in the circumferential direction, the equiphase plane of the high-frequency signal propagating in the waveguide is substantially concentric. The line connecting the feed point and the multiple slot pairs is substantially orthogonal to the equiphase plane of the high-frequency signal propagating in the waveguide at the position of each of the multiple slot pairs. In this case, the angle between the equiphase plane of the high-frequency signal exciting each of the multiple slot pairs and the multiple slots is constant regardless of the position on the waveguide.

[0067] On the other hand, there is a radial waveguide in which the slow wave factor in the waveguide varies depending on the angle in the circumferential direction (azimuth angle φ) on the waveguide. In this case, the slow wave factor in the waveguide is non-uniform in the circumferential direction. In this case, the equiphase surface of the high-frequency signal propagating in the waveguide is substantially elliptical. In this case, the angle between the equiphase surface of the high-frequency signal and the line connecting the feed point and each of the multiple slots changes depending on the azimuth angle φ. Under such circumstances, in the first reference example, the angle of the slot pair is made proportional to the azimuth angle φ. In the first reference example, the angle between the equiphase surface of the high-frequency signal exciting each of the multiple slots and each of the multiple slots changes depending on the azimuth angle φ. The radiation characteristics of the slot change depending on the angle between the equiphase surface of the propagating wave and the extension direction of the slot. Therefore, in the first reference example, differences in characteristics occur among the multiple slots. If differences in characteristics occur among the multiple slots, for example, the bandwidth of the antenna becomes narrower. If a difference occurs, for example, the polarization characteristics will deteriorate. For example, if an attempt is made to compensate for the difference in characteristics by changing the shape of the slot, the design will become complicated.

[0068] In the embodiment, for example, the second absolute value of the second angular difference β2 is different from the first absolute value of the first angular difference β1. The angular difference β0 is changed according to the azimuth angle φ (see, for example, FIG. 5(a)). This makes it possible to maintain, for example, a wider bandwidth than when the angular difference β0 is constant regardless of the azimuth angle φ (first reference example). For example, it makes it possible to maintain high polarization characteristics. For example, it makes it possible to simplify the design.

[0069] With this configuration, the angle between the line connecting the feed point and each of the multiple slots and the equiphase plane of the high-frequency signal can be made substantially constant for each of the multiple slots. This reduces the difference in characteristics between the multiple slots. The radiation characteristics of the antenna device are improved. There is no need to design a radiating element to compensate for the difference in characteristics. The design of the radiating element is simplified.

[0070] In the embodiment, the configuration of the multiple radiating portions 20 can be modified in various ways. For example, the shape of the first slot 21 may be different from the shape of the second slot 22. The corners of each of these slots may be curved. Each of these slots may have a bowtie shape, for example. Each of these slots may be formed by etching the first conductive layer 41, for example. The multiple radiating portions 20 may be formed by cutting the first conductive layer 41 with a machine tool, for example.

[0071] In the embodiment, the first guided wavelength λ1 is shorter than the second guided wavelength λ2. In this way, the guided wavelengths (e.g., in-guide wavelengths) vary within the plane of the first region 10r. This allows the radiation direction of the electromagnetic waves radiated from the plurality of radiating portions 20 to be tilted with respect to the Z-axis direction without changing the spacing between the plurality of radiating portions 20. This, for example, suppresses grating lobes. For example, high efficiency can be maintained. For example, high design freedom can be maintained. The high design freedom can improve the performance of the antenna. According to the embodiment, it is possible to provide an antenna device capable of improving characteristics. In the embodiment, the spacing between the plurality of radiating portions 20 may be changed within the plane.

[0072] An example of the configuration of the antenna device will be described below. FIG. 9 is a schematic perspective view illustrating the antenna device according to the first embodiment. As shown in FIG. 9, the X-axis and Y-axis can be set. The origin OP of these axes corresponds to the feed point 10c. As shown in FIG. 9, the X-axis and Y-axis are aligned with the first region 10r. The Y-axis is perpendicular to the X-axis. The X-axis may be a single reference axis. The angle between the direction from the feed point 10c to the first partial region 11 and the X-axis is defined as angle φ0. The angle φ0 corresponds to the angle of the circumferential direction (direction of the azimuth angle φ) of the direction from the feed point 10c to the first partial region 11 with respect to the X-axis. The angle between the direction from the feed point 10c to the second partial region 12 and the X-axis corresponds to angle (φ0 + 180°).

[0073] For example, the first guided wavelength λ1 corresponds to the guided wavelength in the direction of angle φ0, and the second guided wavelength λ2 corresponds to the guided wavelength in the direction of angle (φ0+180°).

[0074] For example, the third guided wavelength λ3 corresponds to the guided wavelength in the direction of angle (φ0+90°), and the fourth guided wavelength λ4 corresponds to the guided wavelength in the direction of angle (φ0-90°).

[0075] The multiple radiators 20 are capable of radiating first electromagnetic waves 91. The first electromagnetic waves 91 correspond to a high-frequency signal propagating through the waveguide 10w. A main radiation direction 91D of the first electromagnetic waves 91 is tilted with respect to the Z-axis direction. A tilt angle θ0 between the main radiation direction 91D and the Z-axis direction is greater than 0°. A projection direction 91P of the main radiation direction 91D onto the waveguide 10w is along a direction 91z from the second partial region 12 to the first partial region 11.

[0076] For example, in the antenna device 110, a beam-tilted first electromagnetic wave 91 is radiated. For example, in the direction opposite to the tilt direction (second partial region 12), the spacing between the multiple radiating portions 20 is prevented from becoming extremely narrow. This increases the degree of freedom in designing the sizes and positions of the multiple radiating portions 20. This improves the performance of the antenna.

[0077] FIG. 10 is a schematic plan view illustrating the antenna device according to the first embodiment. 10, the multiple radiating portions 20 include radiating portion 20i, radiating portion 20j, and radiating portion 20k. The positions of radiating portion 20i, radiating portion 20j, and radiating portion 20k are different from one another. Radiating portion 20i is adjacent to radiating portion 20j in the circumferential direction. Radiating portion 20k is adjacent to radiating portion 20j in the radial direction. The radial direction corresponds to a direction that passes through feed point 10c and follows first plane PL1.

[0078] In FIG. 10, the distance between the radiation portion 20i and the radiation portion 20j in the circumferential direction is defined as the circumferential distance S φ The distance between the radiation portion 20j and the radiation portion 20k in the radial direction is defined as the radial distance S ρ The circumferential spacing S φ is the distance along the circumferential direction between the center of one of the plurality of radiating portions 20 in the circumferential direction and the center of an adjacent one of the plurality of radiating portions 20 in the circumferential direction. ρ is the distance along the radial direction between the center of one of the plurality of radiating portions 20 in the radial direction and the center of an adjacent one of the plurality of radiating portions 20 in the radial direction.

[0079] As already described with reference to FIG. 3 , one of the multiple radiating sections 20 includes a slot pair 20p. The slot pair 20p includes a first slot 21 and a second slot 22. The coordinates of the center of the first slot 21 are (x1, y1). The coordinates of the center of the second slot 22 are (x2, y2). In the embodiment, for example, at the center 20z of the slot pair 20p, the absolute value of x1 is the same as the absolute value of x2. At the center 20z of the slot pair 20p, the absolute value of y1 is the same as the absolute value of y2.

[0080] 9, the main radiation direction 91D of the first electromagnetic waves 91 radiated from the plurality of radiation portions 20 is set to (θ, φ)=(θ0, φ0). When the circumferential spacing S φThe circumferential spacing S can be set to a relatively free value independent of the main radiation direction 91D. φ may vary depending on the position on the waveguide 10w. For example, the slow wave factor of the waveguide 10w at the position of the radiating portion 20i is expressed as the slow wave factor ξ i The slow wave factor of the waveguide 10w at the position of the radiation portion 20j is expressed as the slow wave factor ξ j For example, the circumferential spacing S φ is,ξ i λ0 and ξ j λ0, the circumferential spacing S φ The upper limit of may vary depending on the position on the waveguide 10w.

[0081] In this way, the circumferential spacing S between the plurality of radiating portions 20 in the circumferential direction around the first axis direction Dz1 is φ may be smaller than ξλ0. One of the multiple radiating portions 20 is adjacent to another of the multiple radiating portions 20 in the circumferential direction. For example, the slow wave factor of the high frequency signal in the one of the multiple radiating portions 20 is equal to or greater than the slow wave factor of the high frequency signal in the other one of the multiple radiating portions. In this case, "ξ" is the slow wave factor of the high frequency signal in the one of the multiple radiating portions 20. "λ0" is the wavelength of the high frequency signal in free space.

[0082] On the other hand, the radial spacing S ρ can be set to an appropriate value, thereby forming a phase distribution on the plane for beam tilt. In an embodiment, the radial spacing S ρ may satisfy the first formula below.

number

[0083] In the first equation, ξ represents the slow wave factor in the waveguide 10w. For example, the relative dielectric constant ε r The dielectric 38 having the slow wave structure of the first member 30 is formed. In this case, ξ=(ε r ) -1 / 2 It is expressed as:

[0084] If the slow wave factor ξ in the radial waveguide is uniform within the waveguide 10w, the radial spacing S ρ changes depending on the azimuth angle φ. For example, when φ=φ0+180°, the radial spacing S between the multiple radiating portions 20 is ρ is the minimum. The radial spacing S ρ The minimum value of min(S ρ ) can be expressed by the following second equation:

number

[0085] On the other hand, when φ=φ0, the radial spacing S between the multiple radiation portions 20 ρ is the maximum radial spacing S ρ The maximum value of max(S ρ ) can be expressed by the following third equation:

number

[0086] FIG. 11 is a graph illustrating the characteristics of the antenna device. FIG. 11 corresponds to a reference example. In this reference example, the slow wave factor ξ is constant throughout the entire waveguide 10w. FIG. 11 illustrates the characteristics when the slow wave factor ξ is changed in this reference example. The horizontal axis of FIG. 11 is the slow wave factor ξ. The vertical axis is the minimum value min(S ρ ), or maximum value max(S ρ ) In FIG. 11, the coefficient α is 1.0. The tilt angle θ0 is 30°.

[0087] As shown in Fig. 11, when the slow wave ratio ξ is low, the minimum value min(S ρ ), and the maximum value max(S ρ ) decreases. When the slow wave ratio ξ is lower than 0.5, the maximum value max(S ρ ) is smaller than λ0 / (1 + |sinθ0|). In this case, grating lobes are practically not generated.

[0088] On the other hand, when the slow wave ratio ξ is lower than 0.5, the minimum value min(S ρ ) is smaller than 0.4λ0. For example, in the slot pair 20p, a slot having a length of about 0.5λ0 at maximum is used. Furthermore, for example, the interval between the plurality of slot pairs 20p is about λ g / 4, which suppresses reflection. For this reason, it is difficult to arrange the slot pairs 20p in areas where the element spacing is narrow. To arrange the slot pairs 20p, short slots with a small amount of radiation are used. For example, narrowing the spacing between the slot pairs 20p at the expense of reflection reduces the degree of freedom in design. Furthermore, the performance of the antenna deteriorates.

[0089] In contrast to this, in the embodiment, the slow wave factor ξ in the radial waveguide is appropriately controlled in accordance with the azimuth angle φ. As a result, the radial spacing S ρ can be kept within a desired range (e.g., substantially constant).

[0090] For example, the following fourth equation can be derived from the first equation.

number

[0091] Radial spacing S ρ When is αλ0 / (1+sinθ0), Equation 5 can be derived from Equation 4. The coefficient α is a real number between 0 and 1.

number

[0092] Equation 5 and ξ=(ε r ) -1 / 2 From this relationship, the following sixth equation can be derived.

[0093]

number

[0094] For example, the slow wave ratio ξ of the first member 30 is changed according to the azimuth angle φ in accordance with Equation 5. This allows the radial spacing S ρ The radial spacing S can be made constant. ρ When is smaller than λ0 / (1+|sinθ0|), grating lobes do not substantially occur.

[0095] For example, according to the sixth formula, the effective relative dielectric constant ε of the first member 30 is r is changed depending on the azimuth angle φ. This allows the radial spacing S ρ The radial spacing S can be made constant. ρ When is smaller than λ0 / (1+|sinθ0|), grating lobes do not substantially occur.

[0096] 12 to 15 are graphs illustrating the characteristics of the antenna device according to the first embodiment. FIG. 12 shows an example of the distribution of the slow wave factor ξ of the first member 30. The horizontal axis of FIG. 12 is the angle difference Δφ. The angle difference Δφ is (φ-φ0). The vertical axis is the slow wave factor ξ1. The slow wave factor ξ1 does not depend on the azimuth angle φ, but varies depending on the radial spacing S between the multiple radiating portions 20. ρ is the slow wave factor ξ, which is essentially 0.90λ0 / (1 + |sinθ0|). "0.90λ0 / (1 + |sinθ0|)" is essentially 0.60λ0. In the example of FIG. 12, the coefficient α in the fifth equation is 0.9. The tilt angle θ0 is 30°.

[0097] As shown in Fig. 12, when the angle difference Δφ is 0°, the slow wave factor ξ1 is set to be low. When the angle difference Δφ is 180°, the slow wave factor ξ1 is set to be high. This allows, for example, the radial spacing S between the multiple radiating portions 20 to be adjusted independently of the azimuth angle φ. ρ is substantially 0.90λ0 / (1+|sinθ0|). The direction in which the angle difference Δφ is 0° corresponds to the beam tilt direction. The direction in which the angle difference Δφ is 180° corresponds to the direction opposite to the beam tilt direction. Due to such a distribution of the slow wave rate ξ1, for example, the radial spacing S ρ can be made substantially constant.

[0098] FIG. 13 shows the effective relative dielectric constant ε in the waveguide 10w in one example. r1 The horizontal axis of FIG. 13 represents the angle difference Δφ, and the vertical axis represents the effective relative dielectric constant ε r1 The effective relative permittivity ε r1 is independent of the azimuth angle φ and is the radial spacing S between the multiple radiating sections 20. ρ However, the effective relative permittivity ε is essentially 0.90λ0 / (1+|sinθ0|). r1 In the example of Figure 13, the coefficient α in the sixth equation is 0.9, and the tilt angle θ0 is 30°.

[0099] As shown in Figure 13, when the angle difference Δφ is 0°, the effective relative dielectric constant ε r1 is set high. When the angle difference Δφ is 180°, the effective relative dielectric constant ε r1 is set low. This allows the radial spacing S between the multiple radiating portions 20 to be adjusted independently of the azimuth angle φ. ρ However, it is practically 0.90λ0 / (1+|sinθ0|). Such an effective relative dielectric constant ε r1 The radial spacing S between the multiple radiating portions 20 is ρ However, it can be kept constant.

[0100] FIG. 14 illustrates the thickness distribution of the dielectric 38 in the waveguide 10w in one example. The thickness corresponds to the length along the Z-axis direction. The horizontal axis of FIG. 14 is the angle difference Δφ. The vertical axis is the ratio HD. The ratio HD is the ratio of the thickness of the dielectric 38 to the distance along the Z-axis direction between the second conductive layer 42 and the first conductive layer 41. The ratio HD is independent of the azimuth angle φ and is proportional to the radial spacing S of the multiple radiating portions 20. ρ However, the effective relative permittivity ε is essentially 0.90λ0 / (1+|sinθ0|). r1 In the example of FIG. 14, the coefficient α in the sixth equation is 0.9. The tilt angle θ0 is 30°.

[0101] The relative permittivity of dielectric 38 is ε r The effective relative dielectric constant in the waveguide 10w is εr1 The ratio HD is expressed by the sixth equation.

[0102]

number

[0103] As described above, by appropriately changing the ratio HD according to the azimuth angle φ, the radial spacing S ρ It is possible to prevent the length from becoming excessively short. For example, the area where a plurality of radiating sections 20 (for example, a plurality of slot pairs 20p) are provided is expanded. The degree of freedom in design is improved. The performance of the antenna device 110 is improved.

[0104] FIG. 15 illustrates the distribution of the filling factor of the dielectric 38 in the waveguide in one example. The horizontal axis of FIG. 15 represents the angle difference Δφ, and the vertical axis represents the filling factor DD of the dielectric 38. The filling factor DD of the dielectric 38 does not depend on the azimuth angle φ, but rather depends on the radial spacing S of the multiple radiating portions 20. ρ However, the effective relative permittivity ε is essentially 0.90λ0 / (1+|sinθ0|). r1 In the example of FIG. 15, the coefficient α in the sixth equation is 0.9. The tilt angle θ0 is 30°. The relative dielectric constant ε of the dielectric 38 is r is 5.

[0105] The filling factor DD of the dielectric 38 is the effective relative dielectric constant ε r1 , the relative permittivity ε of the dielectric 38 r Ratio to (ε r1 / ε r In the embodiment, the distribution of the filling factor DD of the dielectric 38 is appropriately changed depending on the azimuth angle φ. ρIt is possible to prevent the length from becoming excessively short. For example, the area in which a plurality of radiating sections 20 (for example, a plurality of slot pairs 20p) are provided is expanded. The degree of freedom in design is improved. Performance is improved.

[0106] For example, in the embodiment, the first member 30 including the dielectric 38 has an effective relative dielectric constant ε r1 The relative permittivity can be easily lowered in the low region. For example, the dielectric loss can be reduced.

[0107] In the embodiment, the radial spacing S between the plurality of radiating portions 20 in the radial direction ρ is preferably smaller than λ0 / (1+sinθ0). This effectively suppresses grating lobes. As already explained, "λ0" is the wavelength of a high-frequency signal in free space. "θ0" is the angle between the direction perpendicular to the first region 10r (first axis direction Dz1) and the main radiation direction 91D of the first electromagnetic wave 91 radiated from the multiple radiating portions 20 (see FIG. 9).

[0108] As already described, one of the multiple radiating sections 20 may include a slot pair 20p. This, for example, suppresses reflections in the two slots. This makes it possible to reduce reflections in the multiple radiating sections 20. For example, the performance of the antenna can be improved by adjusting the length of the slot, the width of the slot, the position of the slot, and the distance between the two slots.

[0109] In an embodiment, the multiple radiators 20 may be configured to radiate circularly polarized waves. For example, radiating circularly polarized waves facilitates wireless communication and the like, regardless of the polarization direction of the radiated first electromagnetic wave 91. In an embodiment, the circularly polarized waves may be polarized waves including elliptically polarized waves. For example, the multiple radiators 20 may be configured to transmit and receive at least one of right-handed circularly polarized waves and left-handed circularly polarized waves.

[0110] In the embodiment, each of the first slot angle δ1 and the second slot angle δ2 (see FIG. 3) may be substantially 45°. In this case, the first slot 21 and the second slot 22 radiate linearly polarized waves that are substantially orthogonal to each other. For example, the absolute value of the first slot angle δ1 may be substantially the same as the absolute value of the second slot angle δ2, and the first slot length L1 may be substantially the same as the second slot length L2. In this case, the amplitude of the electromagnetic wave radiated by the first slot 21 is substantially the same as the amplitude of the electromagnetic wave radiated by the second slot 22. For example, the circular polarization characteristics of the slot pair 20p are improved.

[0111] For example, the first slot 21 and the second slot 22 may be arranged so that the linearly polarized wave emitted by the first slot 21 in the main radiation direction 91D and the linearly polarized wave emitted by the second slot 22 in the main radiation direction 91D are perpendicular to each other.

[0112] The first slot length L1 and the second slot length L2 may be set so that the amplitude of the linearly polarized wave radiated from the first slot 21 in the main radiation direction 91D is substantially the same as the amplitude of the linearly polarized wave radiated from the second slot 22 in the main radiation direction 91D.

[0113] As already explained, the plurality of radiating portions 20 may be arranged in a substantially spiral shape. For example, the structure of the feed point 10c can be simplified. For example, a coaxial cable may be connected to the center of the radial waveguide, and the plurality of spiral radiating portions 20 can be excited by coaxial mode feeding.

[0114] As already explained, the multiple radiating portions 20 may be arranged substantially concentrically. For example, good radiation characteristics can be obtained even in a small-scale antenna device with a small number of multiple radiating portions 20. For example, the waveguide 10w is fed in a rotational mode. The multiple concentric radiating portions 20 can simplify the structure of the feed point 10c. In a concentric arrangement, for example, the symmetry of the arrangement of the multiple radiating portions 20 is good. Good radiation characteristics can be easily obtained even in a small-scale antenna device 110.

[0115] In the embodiment, electromagnetic waves are radiated (transmitted) from the antenna device 110. In the embodiment, the antenna device 110 may receive electromagnetic waves. For example, the antenna device 110 may receive electromagnetic waves arriving from a direction at an angle (θ0, φ0).

[0116] 16(a) and 16(b) are schematic plan views illustrating the characteristics of the antenna device. These figures illustrate the distribution of equiphase fronts of a high-frequency signal propagating within the waveguide 10w. In FIG. 16(a), the slow wave factor of the waveguide 10w is constant regardless of the azimuth angle φ. In FIG. 16(a), the slow wave factor of the waveguide 10w corresponds to a state in which the coefficient α in Equation 5 is 0.9 and the tilt angle θ is 0°. The slow wave factor of the waveguide 10w is 0.9 regardless of the azimuth angle φ. The guided wavelength of the waveguide 10w does not change even if the azimuth angle φ changes. In FIG. 16(a), the equiphase front 50 within the waveguide 10w is approximately concentric with the feed point 10c as its center.

[0117] In Fig. 16(b), the slow wave factor of the waveguide 10w is given by Equation 5. In Fig. 16(b), the coefficient α in Equation 5 is 1.0, the tilt angle θ0 is 30°, and the angle φ0 is 0°. In Fig. 16(a) and Fig. 16(b), the radial distance between multiple equiphase surfaces 50 at one azimuth angle φ corresponds to the guided wavelength at that azimuth angle φ.

[0118] In the positive direction of the X axis, the radial distance between the equal-phase surfaces 50 corresponds to the first guided wavelength λ1. In the negative direction of the X axis, the radial distance between the equal-phase surfaces 50 corresponds to the second guided wavelength λ2.

[0119] In Fig. 16(b), the guided wavelength of the waveguide 10w varies depending on the azimuth angle φ. In Fig. 16(b), the equiphase surface 50 in the waveguide 10w is substantially elliptical with the feed point 10c as one of its foci.

[0120] For example, in FIG. 16(a), an equiphase surface 50 of a high-frequency signal propagating through the waveguide 10w is substantially perpendicular to the X-axis direction and the Y-axis direction.

[0121] 16(b), the equiphase surface 50 is substantially perpendicular to the X-axis direction but tilted with respect to the Y-axis direction. This is because, in FIG. 16(b), the slow wave ratio of the first member 30 of the waveguide 10w varies depending on the azimuth angle φ. When the slow wave ratio of the first member 30 varies depending on the azimuth angle φ, the equiphase surface 50 becomes substantially elliptical.

[0122] FIG. 17 is a schematic plan view illustrating a part of the antenna device according to the first embodiment. In the following description, the P axis and the R axis represent axes that are perpendicular to each other. The Z axis direction is perpendicular to the P axis and the R axis. The P axis and the R axis are along the XY plane. The R axis is along a straight line that passes through the feed point 10c and the center 20z of the slot pair 20p.

[0123] As shown in FIG. 17, the slot pair 20p includes a first slot 21 and a second slot 22. The equiphase surface 50 corresponds to the equiphase surface of the high-frequency signal propagating in the waveguide 10w at the center 20z of the radiation section 20 (slot pair 20p). A normal vector 50N of the equiphase surface 50 is perpendicular to the equiphase surface 50. The angle between the first slot direction Ds1 and the equiphase surface 50 is defined as a first angle δi1. The angle between the second slot direction Ds2 and the equiphase surface 50 is defined as a second angle δi2. The range of values ​​of the first angle δi1 and the second angle δi2 is not less than −90° and not more than +90°.

[0124] In the first reference example, the multiple radiating sections 20 (multiple slot pairs 20p) are arranged rotated at an angle proportional to the azimuth angle φ. In the first reference example, the straight lines connecting the feed point 10c and the centers 20z of the multiple slot pairs 20p are along the R axis. The equiphase surface 50 of the high-frequency signal propagating in the waveguide 10w is the same as the example shown in FIG. 16(a).

[0125] In FIG. 17, the angle between the equiphase surface 50 and the P axis is the equiphase surface angle φ iIn the example shown in FIG. 16(a), when the slot pair 20p is rotated and arranged at an angle proportional to the azimuth angle φ, the equiphase surface angle φ i can be a value different from 0°. i is different from 0°, even if the first slot angle δ1 is the same as the second slot angle δ2, the first angle δi1 may be different from the second angle δi2 depending on the azimuth angle φ.

[0126] The characteristics of the slots on the waveguide 10w change depending on the angle between the equiphase surface 50 at the slot position and the long axis direction of the slot. For example, the characteristics of the first slot 21 change depending on the first angle δi1. The characteristics of the second slot 22 change depending on the second angle δi2. In each of the multiple slot pairs 20p, when a line connecting the feed point 10c and each center 20z of the multiple slot pairs 20p is along the R axis, a difference occurs between the characteristics of the first slot 21 and the characteristics of the second slot 22. For example, when the first angle δi1 is different from the second angle δi2, a difference occurs in the radiated power between the first slot 21 and the second slot 22. For example, a difference occurs in the frequency characteristics between the first slot 21 and the second slot 22. When the first angle δi1 is different from the second angle δi2, the radiation characteristics of the slot pair 20p deteriorate. When the first angle δi1 is different from the second angle δi2, the bandwidth of the slot pair 20p becomes narrower.

[0127] 18(a) and 18(b) are graphs illustrating the characteristics of the antenna device according to the embodiment. FIG. 18(a) shows the equiphase surface angle φ in one example. i The horizontal axis of FIG. 18(a) is the angle difference Δφ. The angle difference Δφ is φ-φ0. The vertical axis is the angle φ. i1 The angle φ i1 is the angle between the equiphase surface 50 in the waveguide 10w at the azimuth angle φ and the P axis. The slow wave ratio of the waveguide 10w is determined by the radial spacing S of the multiple radiating sections 20 on the waveguide 10w. ρis a value that is substantially 0.90λ0 / (1 + |sinθ0|) regardless of the azimuth angle φ. This value is determined by Equation 5. In the example of FIG. 18(a), the coefficient α in Equation 5 is 0.9, and the tilt angle θ0 is 30°.

[0128] As shown in FIG. 15(a), when the angle difference Δφ is 0°, 180°, or 360°, the angle φ i1 When the angle difference Δφ is different from 0°, 180° or 360°, the angle φ i1 is different from 0°. Angle φ i1 varies depending on the angle difference Δφ. i1 is different from 0°, the first angle δi1 is different from the second angle δi2.

[0129] FIG. 18(b) shows the equiphase surface angle φ in one example. i The horizontal axis of FIG. 18(b) is the angle difference Δφ, and the vertical axis is the angle φ. i1 The slowing rate of the waveguide 10w is determined by the radial spacing S between the multiple radiating portions 20 on the waveguide 10w. ρ is a value that is independent of the azimuth angle φ and is substantially 0.90λ0 / (1 + |sinθ0|). This value is determined by Equation 5. In the example of FIG. 15(b), the coefficient α in Equation 5 is 0.9, and the tilt angle θ0 is 15°, 30°, or 45°.

[0130] As shown in Figure 18(b), when the angle difference Δφ is 0°, 180°, or 360°, the angle φ i1 When the angle difference Δφ is different from 0°, 180° or 360°, the angle φ i1 is different from 0°. i1 varies depending on the angle difference Δφ. i1 varies depending on the tilt angle θ0. When the tilt angle θ0 is large, the angle φ i1 The change in

[0131] FIG. 19 is a graph illustrating the antenna device according to the first embodiment. FIG. 19 illustrates the arrangement angle of the slot pairs 20p in one example. The horizontal axis of FIG. 19 is the angle difference Δφ. The angle difference Δφ is φ-φ0. The vertical axis is the arrangement angle SA of the slot pairs 20p. The arrangement angle SA of the slot pairs 20p is an angle along the circumferential direction. The arrangement angle SA is the angle between the R axis of each of the multiple slot pairs 20p arranged on the waveguide 10w and a line that runs along the direction of φ=φ0 and passes through the feed point 10c. The slow wave ratio of the waveguide 10w is determined by the radial spacing S of the multiple radiating sections 20 on the waveguide 10w. ρ is a value that is substantially 0.90λ0 / (1 + |sinθ0|) regardless of the azimuth angle φ. This value is determined by the fifth equation. In the example of FIG. 19, the coefficient α in the fifth equation is 0.9, and the tilt angle θ0 is 30°. FIG. 19 illustrates the characteristics of the antenna device 110 according to the embodiment and the characteristics of the antenna device 119 of the first reference example.

[0132] As shown in FIG. 19, in the antenna device 119 of the first reference example, the arrangement angle SA is proportional to the angle difference Δφ.

[0133] On the other hand, in the antenna device 110, the arrangement angle SA is not proportional to the angle difference Δφ. In the antenna device 110, the arrangement angle SA is Δφ+φ i The angle of the equiphase surface φ i corresponds to the angle between the equiphase surface 50 and the P axis at the center 20z of each of the plurality of slot pairs 20p. In the antenna device 110, the equiphase surface angle φ i can be made substantially 0°. For example, the first slot angle δ1 in each of the multiple slot pairs 20p is substantially equal to the second slot angle δ2. In this case, the first angle δi1 and the second angle δi2 are substantially equal to each other regardless of the azimuth angle φ. This improves the radiation characteristics of the slot pair 20p. The band of the slot pair 20p can be widened.

[0134] For example, in the embodiment, the slot pair 20p is configured to radiate a circularly polarized wave. In this case, the arrangement angle SA of the plurality of slot pairs 20p is set as in the antenna device 119, and the radial interval S ρ If is constant, the radiation phase in the main radiation direction 91D is substantially the same for the plurality of slot pairs 20p.

[0135] In the embodiment, the plurality of slot pairs 20p are configured to radiate circularly polarized waves. In the embodiment, the arrangement angle SA of the plurality of slot pairs 20p is set as shown by the solid line in Fig. 19. The radiation phase in the main radiation direction 91D varies depending on the positions of the plurality of slot pairs 20p. The difference in radiation phase from the plurality of slot pairs 20p is determined by the equiphase plane angle φ i The radiation phase of the plurality of slot pairs 20p can be adjusted by changing the positions of the plurality of slot pairs 20p. By adjusting the positions of the plurality of slot pairs 20p, the radiation phase in the main radiation direction 91D can be made substantially in-phase for the plurality of slot pairs 20p. This improves the characteristics of the antenna device.

[0136] In the embodiment, in each of the multiple radiating portions 20, the first position is the position of the first slot 21 on the waveguide 10w. In each of the multiple radiating portions 20, the second position is the position of the second slot 22 on the waveguide 10w. In each of the multiple radiating portions 20, the first angle δi1 is the angle between the equiphase front 50 of the high-frequency signal propagating within the waveguide at the first position on the waveguide 10w and the first slot direction Ds1. In each of the multiple radiating portions 20, the second angle δi2 is the angle between the equiphase front 50 at the second position on the waveguide 10w and the second slot direction Ds2. In the embodiment, in the multiple radiating portions 20, the absolute value of the first angle δi1 may be substantially the same as the absolute value of the second angle δi2. For example, the absolute value of the first angle δi1 in the first radiating portion 20a (first absolute angle value) is substantially the same as the absolute value of the second angle δi2 in the first radiating portion 20a (second absolute angle value). For example, the absolute value of the first angle δi1 in the second radiating portion 20b (third absolute angle value) is substantially the same as the absolute value of the second angle δi2 in the second radiating portion 20b (fourth absolute angle value).

[0137] As already explained, in a radial line slot antenna in which the beam tilt is achieved by controlling the slow wave factor in the waveguide 10w, the equal phase surface 50 becomes elliptical due to the non-uniformity of the slow wave factor. The radiated power of the slot varies depending on the angle between the direction of extension of the slot and the equal phase surface 50. In the first reference example in which the slot pairs 20p are arranged rotated by an amount proportional to the azimuth angle φ, the angle between each of the two slots and the equal phase surface 50 deviates from 45°. In the first reference example, differences in characteristics occur among the multiple slot pairs 20p, resulting in a narrow bandwidth. In the embodiment, the absolute value of the first angle δi1 is substantially the same as the absolute value of the second angle δi2. This suppresses differences in characteristics among the multiple slot pairs 20p. A wide bandwidth is obtained.

[0138] For example, when the equiphase surface 50 is a curved surface with a small radius of curvature, there is a large difference in the angle of the equiphase surface 50 at each position of the two slots included in the slot pair 20p. In this case, the arrangement angle SA of the two slots may be adjusted at each position of the two slots included in the slot pair 20p.

[0139] On the other hand, when the equiphase surface 50 is a curved surface with a large radius of curvature, the equiphase surface 50 can be approximated to a plane. In this case, adjustment of the arrangement angle SA of each of the two slots included in the slot pair 20p may be omitted. In this case, only the arrangement angle SA of the slot pair 20p may be adjusted. For example, the above-mentioned position of the first slot 21 on the waveguide 10w may be approximated by the position of the midpoint between the first slot 21 and the second slot 22. For example, the above-mentioned position of the second slot 22 on the waveguide 10w may be approximated by the position of the midpoint between the first slot 21 and the second slot 22.

[0140] In the embodiment, the multiple radiating portions 20 function as an array antenna. Each of the multiple radiating portions 20 may include a slot pair 20p. One of the multiple radiating portions 20 may include a single slot antenna. One of the multiple radiating portions 20 may include a helical antenna. One of the multiple radiating portions 20 may include a patch antenna. One of the multiple radiating portions 20 may include a dipole antenna. One of the multiple radiating portions 20 may include a dielectric resonator antenna. One of the multiple radiating portions 20 may include a leaky wave antenna. Various configurations can be applied to the multiple radiating portions 20.

[0141] The curvature of the equiphase surface 50 of the high-frequency signal propagating through the waveguide 10w varies depending on the position within the waveguide 10w. The curvature of the equiphase surface 50 is high at positions close to the feed point 10c. The curvature of the equiphase surface 50 is low at positions far from the feed point 10c. At positions where the distance from the feed point 10c is sufficiently long compared to λ0, the equiphase surface 50 can be approximated to a straight line (plane).

[0142] FIG. 20 is a schematic plan view illustrating a part of the antenna device according to the first embodiment. 20, in the antenna device 111 according to the embodiment, the curvatures of the plurality of equal phase surfaces 50 (such as the first equal phase surface 50a and the second equal phase surface 50b) are different from one another. The first equal phase surface 50a corresponds to the equal phase surface of the high-frequency signal propagating through the waveguide 10w that passes through the center of the first slot 21. The second equal phase surface 50b corresponds to the equal phase surface of the high-frequency signal propagating through the waveguide 10w that passes through the center of the second slot 22.

[0143] The first tangent 50at corresponds to the tangent to the first equal phase surface 50a at the center of the first slot 21. The second tangent 50bt corresponds to the tangent to the second equal phase surface 50b at the center of the second slot 22. The first angle δi1 corresponds to the angle between the first slot direction Ds1 and the first tangent 50at. The second angle δi2 corresponds to the angle between the second slot direction Ds2 and the second tangent 50bt. First tangent angle φ t1 corresponds to the angle between the first tangent 50at and the P axis. The second tangent angle φ t2 corresponds to the angle between the second tangent 50bt and the P axis. In Fig. 20, the R axis is along the line connecting the feed point 10c and the center 20z of the slot pair 20p.

[0144] In the plurality of slot pairs 20p, the first slot angle δ1 and the second slot angle δ2 (see FIG. 17) are substantially the same, and the plurality of slot pairs 20p are rotated by an arrangement angle SA illustrated by a solid line in FIG. 19. In the example of the slot pair 20p shown in FIG. 20, the first tangent angle φ t1 The absolute value of the second tangent angle φ t2 19. In this case, the first angle δi1 may be different from the absolute value of the second angle δi2. For example, in a region where the curvature of the equiphase surface 50 of the high-frequency signal propagating through the waveguide 10w is high, the first slot angle δ1 is substantially equal to the second slot angle δ2 in one of the plurality of slot pairs 20p. Furthermore, the plurality of slot pairs 20p are rotated by an arrangement angle SA illustrated by the solid line in FIG. 19. In this case, the first angle δi1 may have a value different from the second angle δi2.

[0145] For example, the first tangent angle φ t1 and the second tangent angle φt2 The first slot 21 and the second slot 22 may be arranged so that the first angle δi1 is substantially equal to the second angle δi2, taking into consideration the value of δi1. This improves the radiation characteristics of the slot pair 20p. The band can be widened in the slot pair 20p. The characteristics of the antenna device are improved. In the antenna device 111, the first slot angle δ1 may be different from the second slot angle δ2.

[0146] 21(a) and 21(b) are schematic views illustrating the antenna device according to the first embodiment. Figure 21(a) is a plan view, and Figure 21(b) is a cross-sectional view. As shown in FIG. 21(a), in an antenna device 112 according to the embodiment, the waveguide 10w is a rectangular waveguide. In the antenna device 112, the rectangular waveguide of the waveguide 10w may be formed, for example, by cutting a metal. The rectangular waveguide of the waveguide 10w may be, for example, a substrate integrated waveguide (SIW). The SIW may be formed using, for example, a dielectric substrate. In the antenna device 112, the multiple radiating portions 20 may be slots provided in the waveguide 10w.

[0147] 21(b), in the antenna device 112, the first region 10r includes a first partial region 11 and a second partial region 12. A first guided wavelength λ1 in the waveguide in the first partial region 11 is shorter than a second guided wavelength λ2 in the waveguide in the second partial region 12.

[0148] In the embodiment, the waveguide 10w may be a rectangular waveguide. The waveguide 10w may be, for example, a ridge waveguide. The waveguide 10w may be, for example, a gap waveguide. The waveguide 10w may be, for example, a parallel plate waveguide. The waveguide 10w may be, for example, a dielectric waveguide. In the embodiment, in various waveguides 10w, for example, the slow wave factor ξ in the beam tilt direction is high (the guided wavelength is short) and the slow wave factor ξ in the direction opposite to the beam tilt direction is low (the guided wavelength is long). This suppresses grating lobes without excessively narrowing the spacing between the multiple radiating portions 20.

[0149] In the embodiment, in each of the multiple slot pairs 20p, the angle between the equiphase surface 50 of the high-frequency signal propagating through the waveguide 10w and the first slot direction Ds1 at the position of the first slot 21 is substantially the same as the angle between the equiphase surface 50 of the high-frequency signal propagating through the waveguide 10w and the second slot direction Ds2 at the position of the second slot 22. The antenna device 112 has improved radiation characteristics. Wideband operation is achieved. The characteristics of the antenna device are improved.

[0150] An example of the characteristics of the antenna device will now be described. 22(a) and 22(b) are schematic views illustrating the antenna device according to the first embodiment. Fig. 22(a) is a plan view, and Fig. 22(b) is a cross-sectional view along the RZ plane. In this example, the configuration of the antenna device 110 is applied as the antenna device.

[0151] 22(a) and 22(b) illustrate an analytical model 60 for the antenna device 110. In FIG. 22(a), the X-axis corresponds to the direction in which the azimuth angle φ is 0 in FIG. 2. The waveguide 10w is configured so that the high-frequency signal propagates along the R-axis. In the analytical model 60, the high-frequency signal propagates inside the waveguide 10w along the R-axis from a position at an angle of (Δφ+π) to a position at an angle of Δφ. In the analytical model 60, the equiphase surface 50 of the high-frequency signal is parallel to the P-axis. The angular difference Δφ is φ-φ0.

[0152] The high-frequency signal excites a first slot 21 and a second slot 22 provided in the waveguide 10w. The slot pair 20p includes the first slot 21 and the second slot 22. The slot pair 20p in Fig. 22(a) is rotated by an angle of (Δφ-90°) around the center 20z of the slot pair 20p from the state of the slot pair 20p illustrated in Fig. 3.

[0153] The slot pair 20p is configured to radiate circularly polarized waves. The slot pair 20p may be designed, for example, to have a good axial ratio in the main radiation direction 91D. The axial ratio is the ratio of the major axis length to the minor axis length of the circularly polarized waves radiated by the slot pair 20p. Generally, an antenna is defined as radiating circularly polarized waves when the axial ratio in the main radiation direction of the antenna is 3 dB or less.

[0154] FIG. 23 is a graph illustrating the antenna device according to the first embodiment. Fig. 23 shows the thickness of the dielectric 38 of the first member 30 provided in the waveguide 10w of the antenna device 110. In Fig. 23, the horizontal axis represents the angle difference Δφ, and the vertical axis represents the thickness H1 of the dielectric 38. The thickness H1 is the length along the Z-axis direction.

[0155] The thickness (length in the Z-axis direction) of the waveguide 10w is 4.00 mm. In the example of FIG. 23, the thickness H1 of the dielectric 38 varies depending on the angle difference Δφ. In this example, when the angle difference Δφ is 0°, the thickness H1 is 3.99 mm. When the angle difference Δφ is 90°, the thickness H1 is 3.20 mm.

[0156] The ratio HD is derived from the thickness H1 illustrated in Fig. 23. The ratio HD is the ratio of the thickness H1 of the dielectric 38 to the distance along the Z-axis direction between the second conductive layer 42 and the first conductive layer 41. The ratio HD and the effective relative dielectric constant ε r1 The relationship between the distribution of and is expressed by Equation 7.

[0157] The dielectric 38 is disposed so as to be in contact with the second conductive layer 42. A gap corresponding to the difference in height is provided between the dielectric 38 and the first conductive layer 41. The relative dielectric constant of the dielectric 38 is 5.0.

[0158] In the analytical model 60, a dielectric 38 having the characteristics illustrated in Fig. 23 is provided. In the analytical model 60, the following parameters are applied (see Fig. 3). x1:-2.10mm x2: 2.10mm y1:-2.23mm y2: 2.23mm L1: 8.50mm L2: 8.50mm w1: 0.80mm w2: 0.80mm δ1: 45° δ2: 45°

[0159] The effective relative dielectric constant in the waveguide 10w is determined by the radial spacing S between the multiple radiating portions 20 on the waveguide 10w. ρ is a value that is essentially 0.90λ0 / (1 + |sinθ0|) regardless of the azimuth angle φ. This value is calculated using equation 6. The coefficient α in equation 6 is 0.9. The tilt angle θ0 is 30°. "λ0" is the free space wavelength of the high-frequency signal. The frequency of the high-frequency signal is 12.5 GHz.

[0160] FIG. 24 is a graph illustrating the antenna device according to the first embodiment. FIG. 24 shows an example of the analysis results regarding the characteristics of the slot pair 20p. In Fig. 24, the angular difference Δφ is 90°. The horizontal axis of Fig. 24 is the tilt angle θ. The vertical axis of Fig. 24 is the axial ratio AR1 of the electromagnetic wave radiated by the slot pair 20p. The axial ratio AR1 is the ratio of the major axis length to the minor axis length of the circularly polarized wave radiated by the slot pair 20p in the main radiation direction 91D.

[0161] In Figure 24, the tilt angle θ is 30° in the main radiation direction 91D. The axial ratio AR1 of the slot pair 20p in the main radiation direction 91D is 1.2 dB. Generally, when the axial ratio in the main radiation direction of the antenna is 3 dB or less, the antenna can radiate circularly polarized waves. As illustrated in Figure 24, it can be seen that the slot pair 20p can radiate circularly polarized waves.

[0162] 25(a) and 25(b) are schematic plan views illustrating the antenna device. 25(a) corresponds to a first analytical model 60a. FIG. 25(b) corresponds to a second analytical model 60b. In these analytical models, a first slot 21 and a second slot 22 are provided. The angle between the equiphase surface 50 at the position of the center 20z of the slot pair 20p and the X axis is defined as an angle φ iz 25(a) and 25(b), the X axis is parallel to the direction of φ0=0 in FIG.

[0163] In the first analytical model 60a, the slot pair 20p is arranged so that the R axis is along the line connecting the feed point 10c and the center 20z of the slot pair 20p. iz is -16.6 degrees.

[0164] In the second analytical model 60b, the slot pair 20p is arranged so that the P axis is along the equiphase surface 50. In the second analytical model 60b, the angle φ iz is 0°.

[0165] In the first analytical model 60a, the first angle δi1 between the first slot direction Ds1 and the equiphase surface 50 is different from the second angle δi2 between the second slot direction Ds2 and the equiphase surface 50. In the first analytical model 60a, a difference in characteristics occurs between the first slot 21 and the second slot 22. As a result, the radiation characteristics of the slot pair 20p are poor.

[0166] In the second analytical model 60b, the first angle δi1 is the same as the second angle δi2. This reduces the difference in characteristics between the first slot 21 and the second slot 22. This improves the radiation characteristics of the slot pair 20p.

[0167] FIG. 26 is a graph illustrating the characteristics of the antenna device. Fig. 26 illustrates simulation results of the characteristics related to the first analytical model 60a and the second analytical model 60b. The horizontal axis of Fig. 26 represents the tilt angle θ. The vertical axis represents the axial ratio AR2. The axial ratio AR2 is the axial ratio of the electromagnetic waves radiated by the slot pair 20p in the RZ plane. In the example of Fig. 26, the tilt angle θ is 30° in the main radiation direction 91D.

[0168] 26, in the first analytical model 60a, the axial ratio AR2 is 7.4 dB when the tilt angle θ is 30°. On the other hand, in the second analytical model 60b, the axial ratio AR2 is 2.2 dB when the tilt angle θ is 30°.

[0169] In the first analytical model 60a, the axial ratio AR2 is greater than 3 dB when the tilt angle θ is 30°. In the first analytical model 60a, the slot pair 20p does not operate as a circularly polarized antenna.

[0170] In the second analytical model 60b, the axial ratio AR2 is 3 dB or less when the tilt angle θ is 30°. In the second analytical model 60b, the slot pair 20p operates as a circularly polarized antenna.

[0171] In the embodiment, the slot pair 20p is arranged such that the first angle δi1 is substantially equal to the second angle δi2. iz The slot pair 20p is arranged so that the angle is substantially 0°, thereby improving the characteristics of the antenna device.

[0172] In the first analytical model 60a and the second analytical model 60b, the direction of θ=30° in the RZ plane and the main radiation direction 91D are different from each other. For example, the arrangement position of the slot pair 20p in the waveguide 10w may be optimized so that the axial ratio AR2 in the (θ0, -φ1) direction is favorable. This allows a favorable axial ratio AR2 to be obtained in the main radiation direction 91D of the slot pair 20p. For example, the slot pair 20p is arranged by rotating it at an angle of (Δφ+φ1). This allows favorable characteristics of the slot pair 20p to be obtained in the (θ0, φ0) direction. The characteristics of the antenna device are improved.

[0173] FIG. 27 is a graph illustrating the characteristics of the antenna device. FIG. 27 shows the angle φ iz The horizontal axis of Fig. 28 shows the results of simulation of the characteristics when the angle φ iz The vertical axis of represents the axial ratio AR3 of the slot pair 20p. The axial ratio AR3 is the axial ratio of the slot pair 20p in the RZ plane.

[0174] In FIG. 27, the angle φ at which the axial ratio AR3 at θ=30° is 3 dB or less iz The angle φ is between -1 and +9 degrees. iz When the angle φ is 0°, the axial ratio AR3 is not the best. This characteristic is thought to be due to an error in the design of the slot pair 20p. iz If the axial ratio AR3 is best when θ is 0°, then the angle φ at which the axial ratio AR3 is 3 dB or less at θ=30° iz The angle φ is considered to be in the range of -5° to +5°. iz Good characteristics are obtained when the absolute value of the difference between the first angle δi1 and the second angle δi2 is equal to or less than -5° and equal to or less than 5°. For example, good characteristics are obtained when the absolute value of the difference between the first angle δi1 and the second angle δi2 is equal to or less than 10°.

[0175] 28(a) and 28(b) are graphs illustrating the characteristics of the antenna device. Figure 28(a) illustrates simulation results of characteristics when the second slot length L2 is fixed and the first slot length L1 is changed in the second analytical model 60b. The horizontal axis of Figure 28(a) is the amount of change LD1 in the first slot length L1. When the amount of change LD1 is 0, the first slot length L1 is the same as the second slot length L2. The vertical axis of Figure 28(a) is the axial ratio AR4 of the slot pair 20p in the RZ plane. The tilt angle θ is 30°.

[0176] Figure 28(b) illustrates simulation results of characteristics when the first slot length L1 is fixed and the second slot length L2 is changed in the second analytical model 60b. The horizontal axis of Figure 28(b) represents the amount of change LD2 in the second slot length L2. When the amount of change LD2 is 0, the second slot length L2 is the same as the first slot length L1. The vertical axis of Figure 28(b) represents the axial ratio AR4 of the slot pair 20p in the RZ plane. The tilt angle θ is 30°.

[0177] As shown in FIG. 28(a), when θ=30°, the range of the change LD1 where the axial ratio AR4 is 3 dB or less is from −0.05 mm to 0.80 mm.

[0178] As shown in FIG. 25(b), when θ=30°, the range of the change LD2 where the axial ratio AR4 is 3 dB or less is from −1.16 mm to 0.10 mm.

[0179] When the difference between the first slot length L1 and the second slot length L2 is 1.16 mm or less, good characteristics are obtained.

[0180] In the analytical model 60, the first analytical model 60a, and the second analytical model 60b, "λ0" is the free-space wavelength of the high-frequency signal propagating through the waveguide 10w. The frequency of this high-frequency signal is 12.5 GHz. In this case, "λ0" is substantially 23.98 mm. In this embodiment, the difference between the first slot length L1 and the second slot length L2 is 0.05λ0 or less. Good characteristics can be obtained.

[0181] (Second embodiment) FIG. 29 is a schematic cross-sectional view illustrating the antenna device according to the second embodiment. 29, the antenna device 120 according to this embodiment includes a first driving section 10D. Other configurations of the antenna device 120 may be similar to the configuration of the antenna device according to the first embodiment (such as the antenna device 110).

[0182] The first driving unit 10D is configured to rotate the waveguide 10w within a plane (XY plane) including the first region 10r. By rotating the waveguide 10w, the first electromagnetic waves 91 radiated from the multiple radiating units 20 may be conically scanned.

[0183] The first driving unit 10D may mechanically (physically) rotate the waveguide 10w. For example, conical scanning of the beam (first electromagnetic wave 91) becomes possible. Unlike a phased array that performs beam scanning electronically, beam scanning becomes possible without using circuit elements such as a phase shifter.

[0184] The antenna device 120 may be used as a receiving device. The antenna device 120 can receive electromagnetic waves arriving from a direction at an angle (θ0, φ0), for example.

[0185] FIG. 30 is a schematic perspective view illustrating the antenna device according to the second embodiment. 30, an antenna device 121 according to this embodiment includes a waveguide 10w and a transparent member 15. Other configurations of the antenna device 121 may be similar to those of the antenna device 110 and the like.

[0186] The transmitting member 15 transmits the first electromagnetic waves 91 radiated from the multiple radiating portions 20. The transmitting member 15 may be capable of changing the passing phase of the first electromagnetic waves 91. For example, the direction of the second electromagnetic waves 92 radiated from the transmitting member 15 changes in accordance with the change in the passing phase.

[0187] The transmitting member 15 tilts the beam by, for example, changing the passing phase of the electromagnetic field of the first electromagnetic wave 91. The tilt angle of the beam by the transmitting member 15 may be the same as or different from the tilt angle of the beam in the waveguide 10w.

[0188] 30, the transmitting member 15 includes a plurality of transmitting portions 16. In this example, the distribution of the plurality of transmitting portions 16 varies within the plane.

[0189] 30, the antenna device 121 may further include a second driving unit 15D. The second driving unit 15D is configured to rotate the transmitting member 15. As the transmitting member 15 rotates, the direction of the second electromagnetic wave 92 changes.

[0190] FIG. 31 is a schematic perspective view illustrating the antenna device according to the second embodiment. As shown in Fig. 31, the antenna device 122 according to this embodiment also includes the transparent member 15. In the antenna device 122, the thickness of the transparent member 15 varies within the plane.

[0191] The transmitting member 15 may include a transmit array. The transmit array includes, for example, a plurality of elements (unit cells) with different transmission phases.

[0192] FIG. 32 is a schematic diagram illustrating a part of the antenna device according to the second embodiment. Figure 32 shows an example of one unit cell included in a transmit array. In the example of Figure 32, two dielectric substrates 15a with metal patches are combined with a metal plate 15b with a cross-shaped slot. By changing the rotation angle of the unit cell, the passing phase of the circularly polarized wave can be changed. For example, by further increasing the number of dielectric substrates 15a, the rotation angle of the unit cell can be further increased. The bandwidth of the unit cell can be broadened.

[0193] For example, the transmitting member 15 illustrated in Fig. 30 may be rotated in a plane. For example, the passing phase of a circularly polarized wave can be changed. The transmitting member 15 can tilt the beam by changing the passing phase of an electromagnetic wave, for example. The configuration of the transmitting member 15 can be modified in various ways.

[0194] 33 to 35 are schematic diagrams illustrating the antenna device according to the second embodiment. 33, the rotation angle in the waveguide 10w is defined as a first rotation angle τ1, and the rotation angle in the transmitting member 15 is defined as a second rotation angle τ2.

[0195] 34, for example, when the first rotation angle τ1 in the waveguide 10w is 0, a first electromagnetic wave 91 is radiated from the waveguide 10w in a direction of an angle θ1. An equiphase surface 91a is formed in the first electromagnetic wave 91. The equiphase surface 91a is perpendicular to the direction of the angle θ1. The first electromagnetic wave 91 is radiated in the direction of the angle θ1.

[0196] 35, a passing phase distribution 92a is formed in the transmitting member 15. For example, when a first electromagnetic wave 91 is irradiated onto the transmitting member 15, the transmitting member 15 radiates a second electromagnetic wave 92 in a direction at an angle θ2.

[0197] The transmitting member 15 is placed on the waveguide 10w. In this state, the waveguide 10w is rotated by a first rotation angle τ1, and the transmitting member 15 is rotated by a second rotation angle τ2. In this case, the x-component "kx" and y-component "ky" of the wave number of the second electromagnetic wave 92 transmitted through the transmitting member 15 are expressed by the following Equation 8.

number

[0198] In the eighth formula, the wave number k0 is 2π / λ0, where λ0 is the wavelength in free space of the high-frequency signal transmitted and received by the antenna device.

[0199] From equation 8, the tilt direction (θ0, φ0) of the beam in the antenna device is expressed by equations 9 and 10 below.

number

number

[0200] "k x " and "k y " changes depending on the first rotation angle τ1 of the waveguide 10w and the second rotation angle τ2 of the transmitting member 15. The tilt direction (θ0, φ0) of the beam can be changed by these rotation angles.

[0201] For example, a waveguide 10w with an angle θ1 of 30° or more is combined with a transmitting member 15 with an angle θ2 of 30° or more. The first rotation angle τ1 of the waveguide 10w and the second rotation angle τ2 of the transmitting member 15 are changed (rotated) within a range of -180° or more and 180° or less. As a result, the tilt angle θ0 changes within a range of 0° or more and 90° or less, and the angle φ0 changes within a range of -180° or more and 180° or less. Two-dimensional beam scanning in any direction is possible.

[0202] 36(a) and 36(b) are schematic diagrams illustrating the characteristics of the antenna device according to the second embodiment. These figures illustrate the beam tilt direction (θ0, φ0) when the waveguide 10w and the transmitting member 15 are rotated. In this example, the angles θ1 and θ2 are 30°. The first rotation angle τ1 of the waveguide 10w and the second rotation angle τ2 of the transmitting member 15 are changed within the range of -180° to 180°. The horizontal axis of these figures is the first rotation angle τ1, and the vertical axis is the second rotation angle τ2.

[0203] 36(a), by changing the first rotation angle τ1 and the second rotation angle τ2, the tilt angle θ0 varies within a range of 0° to 90°. For example, when the second rotation angle τ2 is φ1±180°, the tilt angle θ0 is 0°. For example, when the second rotation angle τ2 is the same as the first rotation angle τ1, the tilt angle θ0 is 90°.

[0204] 36(b), by changing the first rotation angle τ1 and the second rotation angle τ2, the angle φ0 changes within a range of -180° to 180°. For example, the first rotation angle τ1 and the second rotation angle τ2 are changed while maintaining a constant difference between them. This allows the angle φ0 to be changed while maintaining a constant tilt angle θ0.

[0205] As described above, the transmitting member 15 may be provided. The transmitting member 15 can change the direction of the first electromagnetic wave 91 emitted from the waveguide 10w. For example, the range of beam scanning can be widened. The transmitting member 15 can be mechanically rotated. The rotation can be performed by a second driving unit 15D. The range of beam scanning can be further widened.

[0206] For example, two-dimensional beam scanning is possible by rotating the waveguide 10w and the transmitting member 15. For example, in a phased array that performs beam scanning electronically, an additional circuit such as a phase shifter is provided. In the embodiment, no additional circuit is required. In the embodiment, for example, beam scanning can be performed at low cost.

[0207] The equiphase surface 91a illustrated in Fig. 34 is linear. In an embodiment, the equiphase surface 91a does not have to be linear. The passing phase distribution 92a illustrated in Fig. 35 is linear. In an embodiment, the passing phase distribution 92a does not have to be linear.

[0208] When the equiphase surface 91a is not linear, the passing phase distribution 92a may be changed to correct the equiphase surface 91a. When the passing phase distribution 92a is not linear, the equiphase surface 91a may be changed to correct the passing phase distribution 92a.

[0209] FIG. 37 is a schematic perspective view illustrating the antenna device according to the second embodiment. 37, in an antenna device 122 according to this embodiment, a rotary joint 10R is provided in addition to a waveguide 10w and a transparent member 15. Other configurations of the antenna device 122 may be similar to those of the antenna device 121 and the like.

[0210] In the antenna device 122, the rotary joint 10R can hold the waveguide 10w and the transparent member 15 at any angle. This prevents the power feeding transmission line from being twisted and damaged when the waveguide 10w and the transparent member 15 are mechanically rotated.

[0211] In the embodiment, the first driving unit 10D and the second driving unit 15D may include a motor or the like.

[0212] The antenna device 120, the antenna device 121, and the antenna device 122 may be used as receiving devices, and may receive, for example, electromagnetic waves arriving from a direction at an angle (θ0, φ0).

[0213] (Third embodiment) FIG. 38 is a schematic diagram illustrating a wireless device according to the third embodiment. 38, a wireless device 210 according to an embodiment includes the antenna device according to the first or second embodiment (for example, the antenna device 110) and an electric circuit 201. The electric circuit 201 is configured to be coupled to a feed point 10c of a waveguide 10w included in the antenna device 110. The electric circuit 201 may be electrically connected to the feed point 10c.

[0214] For example, by providing the electric circuit 201, the antenna device 110 can be used as a wireless communication device, a radar, a wireless power supply device, or the like.

[0215] For example, the electric circuit 201 can supply a high frequency signal to the antenna device 110. The electric circuit 201 causes the antenna device 110 to radiate an electromagnetic wave. When the antenna device 110 receives the electromagnetic wave, the electric circuit 201 can demodulate the high frequency signal.

[0216] In the embodiment, the antenna device (for example, the antenna device 110) and the wireless device 210 can be applied to wireless communication devices using phased arrays, radar, wireless power transmission, or the like.

[0217] In the embodiment, good characteristics can be obtained in the beam-tilted array antenna.

[0218] The embodiments may include the following technical solutions. (Technical proposal 1) a waveguide including a feed point and a first region; the first region is located around the feed point on a first plane intersecting a first axis direction passing through the feed point, the waveguide includes a plurality of radiating portions provided in the first region, each of the plurality of radiating portions includes a first slot extending along a first slot direction and a second slot extending along a second slot direction intersecting the first slot direction; the plurality of radiating portions include a first radiating portion and a second radiating portion, a first radiation portion direction from the feed point to the first radiation portion intersects with the first axis direction, a second radiation portion direction from the feed point to the second radiation portion intersects the first axis direction and intersects the first radiation portion direction; an antenna device, wherein a second absolute value of a second angular difference between the first slot direction in the second radiating portion and the second radiating portion direction is smaller than a first absolute value of a first angular difference between the first slot direction in the first radiating portion and the first radiating portion direction.

[0219] (Technical proposal 2) the plurality of radiating portions further include a third radiating portion; a third radiation portion direction from the feed point to the third radiation portion intersects the first axis direction and intersects the second radiation portion direction, the feed point is located between the third radiating portion and the first radiating portion in a direction along the first radiating portion direction, The antenna device described in Technical Solution 1, wherein a third absolute value of a third angle difference between the first slot direction in the third radiating portion and the third radiating portion direction is greater than the second absolute value.

[0220] (Technical proposal 3) the plurality of radiating portions further include a fourth radiating portion, a fourth radiation portion direction from the feed point to the fourth radiation portion intersects the first axis direction and intersects the first radiation portion direction, the feed point is located between the fourth radiating portion and the second radiating portion in a direction along the second radiating portion direction, The antenna device described in Technical Solution 2, wherein a fourth absolute value of a fourth angle difference between the first slot direction in the fourth radiating portion and the fourth radiating portion direction is greater than the first absolute value.

[0221] (Technical proposal 4) The antenna device according to any one of Technical Solutions 1 to 3, wherein an angle between the first slot direction and the second slot direction is greater than or equal to 80° and less than or equal to 100°.

[0222] (Technical proposal 5) the first slot included in the first radiating portion has a first slot length along the first slot direction, the second slot included in the first radiating portion has a second slot length along the second slot direction, The antenna device according to any one of Technical Schemes 1 to 4, wherein a ratio of an absolute value of a difference between the first slot length and the second slot length to the first slot length is 0.1 or less.

[0223] (Technical proposal 6) the first region includes a first partial region and a second partial region, the feeding point is located between the second partial region and the first partial region in a first intersecting direction intersecting with the first axis direction, the waveguide includes a first member; the first member includes a first member region corresponding to the first partial region and a second member region corresponding to the second partial region; the first member region and the second member region satisfy at least one of a first condition, a second condition, a third condition, a fourth condition, and a fifth condition; In the first condition, a first relative dielectric constant of the first component region is different from a second relative dielectric constant of the second component region, In the second condition, the density of the first holes included in the first component region is different from the density of the second holes included in the second component region, In the third condition, a first average size of the plurality of first holes included in the first component region is different from a second average size of the plurality of second holes included in the second component region; In the fourth condition, a first configuration of the first structure provided in the first component region is different from a second configuration of the second structure provided in the second component region, An antenna device described in any one of Technical Solutions 1 to 5, wherein, in the fifth condition, the thickness of the first component included in the first component region is different from the thickness of the first component included in the second component region.

[0224] (Technical proposal 7) The waveguide is configured to guide a high-frequency signal supplied to the feed point, the first region includes a first partial region and a second partial region, the feeding point is located between the first partial region and the second partial region in a first intersecting direction intersecting with the first axis direction, The antenna device according to any one of Technical Solutions 1 to 5, wherein a first guided wavelength in the waveguide in the first partial region is shorter than a second guided wavelength in the waveguide in the second partial region.

[0225] (Technical proposal 8) In each of the plurality of radiating portions, a first position is a position of the first slot on the waveguide; In each of the plurality of radiating portions, the second position is a position of the second slot on the waveguide; In each of the plurality of radiating portions, a first angle is an angle between an equiphase plane of the high-frequency signal propagating through the waveguide at the first position on the waveguide and the first slot direction; In each of the plurality of radiating portions, a second angle is an angle between the equiphase surface at the second position on the waveguide and the second slot direction; a first absolute angle value of the first angle at the first radiating portion is substantially equal to a second absolute angle value of the second angle at the first radiating portion; The antenna device described in Technical Solution 7, wherein a third absolute angle value of the first angle in the second radiating portion is substantially the same as a fourth absolute angle value of the second angle in the second radiating portion.

[0226] (Technical proposal 9) the plurality of radiators are configured to radiate electromagnetic waves in response to the high-frequency signal; The antenna device according to Technical Solution 7 or 8, wherein the projection direction of the main radiation direction of the electromagnetic wave onto the waveguide is along the direction from the second partial region to the first partial region.

[0227] (Technical proposal 10) the waveguide includes a first member; The antenna device according to Technical Solution 9, wherein a first slow wave rate in the first partial region of the first member is different from a second slow wave rate in the second partial region of the first member.

[0228] (Technical proposal 11) The antenna device described in Technical Solution 10, wherein the first member includes a dielectric.

[0229] (Technical proposal 12) the first guided wavelength is a wavelength of the high-frequency signal propagating along a direction from the feed point to the first partial region; The antenna device according to Technical Solution 7 or 8, wherein the second guided wavelength is the wavelength of the high-frequency signal propagating along the direction from the feed point to the second partial region.

[0230] (Technical proposal 13) a radial distance between the plurality of radiation portions arranged along an intersecting direction intersecting the first axis direction is smaller than λ / {1+sin(θ)}; λ is the wavelength of the high frequency signal in free space, The antenna device described in Technical Proposal 7 or 8, wherein θ0 is the angle between the first axis direction and the main radiation direction of the electromagnetic waves radiated from the multiple radiation portions aligned along the intersecting direction that intersects with the first axis direction.

[0231] (Technical proposal 14) a circumferential spacing between the plurality of radiation portions in a circumferential direction around the first axis direction is smaller than ξλ0, one of the plurality of radiating portions is adjacent to another of the plurality of radiating portions in the circumferential direction; a slow wave rate of the high frequency signal in the one of the plurality of radiating units is equal to or greater than a slow wave rate of the high frequency signal in the other one of the plurality of radiating units; ξ is the slow wave ratio of the high-frequency signal in the one of the plurality of radiators, The antenna device according to Technical Solution 7 or 8, wherein λ0 is the wavelength of the high-frequency signal in free space.

[0232] (Technical proposal 15) the first region includes a third partial region and a fourth partial region, the feed point is located between the third partial region and the fourth partial region; a direction from the feed point to the third partial region intersects with a direction from the feed point to the first partial region; a third guided wavelength in the waveguide in the third subregion is longer than the first guided wavelength and shorter than the second guided wavelength; The antenna device according to any one of Technical Schemes 7 to 14, wherein a fourth guided wavelength in the waveguide in the fourth partial region is longer than the first guided wavelength and shorter than the second guided wavelength.

[0233] (Technical proposal 16) The antenna device according to any one of Technical Schemes 1 to 15, wherein the plurality of radiating sections are configured to transmit and receive at least one of right-handed circularly polarized waves and left-handed circularly polarized waves.

[0234] (Technical proposal 17) The antenna device according to any one of Technical Schemes 1 to 16, wherein the plurality of radiating portions are arranged substantially spirally or concentrically around the feed point.

[0235] (Technical proposal 18) Further comprising a first drive unit, the first drive unit is configured to rotate the waveguide in the first plane; The antenna device according to any one of Technical Schemes 1 to 17, wherein the first electromagnetic waves radiated from the plurality of radiating portions are conically scanned by rotating the waveguide.

[0236] (Technical proposal 19) Further comprising a transparent member, the transmitting member is configured to transmit first electromagnetic waves radiated from the plurality of radiating portions; the transmitting member is configured to change a passing phase of the first electromagnetic wave; The antenna device according to any one of Technical Schemes 1 to 17, wherein the direction of the second electromagnetic wave radiated from the transmitting member changes in accordance with the change in the passing phase.

[0237] (Technical proposal 20) Further comprising a second drive unit, the second drive unit is configured to rotate the transmission member, The antenna device described in Technical Solution 19, wherein the direction of the second electromagnetic wave changes in response to the rotation of the transparent member.

[0238] (Technical proposal 21) An antenna device according to any one of technical proposals 1 to 20; an electrical circuit coupleable to the feed point; A wireless device comprising:

[0239] According to the embodiment, it is possible to provide an antenna device and a radio device that can improve characteristics.

[0240] The above describes embodiments of the present invention with reference to examples. However, the present invention is not limited to these examples. For example, the specific configurations of each element included in the antenna device, such as the waveguide, the transparent member, and the driving unit, are within the scope of the present invention as long as a person skilled in the art can implement the present invention in a similar manner and obtain similar effects by appropriately selecting them from known ranges.

[0241] Any combination of two or more elements of each example within the scope of technical feasibility is also included within the scope of the present invention as long as it encompasses the gist of the present invention.

[0242] All antenna devices and radio devices that can be implemented by a person skilled in the art by making appropriate design modifications based on the antenna device and radio device described above as embodiments of the present invention also fall within the scope of the present invention, as long as they include the gist of the present invention.

[0243] Within the scope of the concept of the present invention, a person skilled in the art may conceive of various modifications and alterations, and it is understood that these modifications and alterations also fall within the scope of the present invention.

[0244] Although several embodiments of the present invention have been described, these embodiments are presented as examples and are not intended to limit the scope of the invention. These novel embodiments can be embodied in various other forms, and various omissions, substitutions, and modifications can be made without departing from the spirit of the invention. These embodiments and their modifications are included within the scope and spirit of the invention, and are also included in the scope of the invention and its equivalents as defined in the claims. [Explanation of symbols]

[0245] 10D: first driving section, 10R: rotary joint, 10c: feeding point, 10r: first region, 10w: waveguide, 11-14: first to fourth partial regions, 15: transparent member, 15D: second driving section, 15a: dielectric substrate, 15b: metal plate, 16: transparent portion, 20: radiating section, 20a-20d: first to fourth radiating sections, 20i-20k: radiating section, 20p: slot pair, 20z: center, 21, 22: first and second slots, 25: coaxial line, 25i: inner conductor, 25o: outer conductor, 30: first member, 31, 32: first and second member regions, 31h, 32h: first and second holes, 38: dielectric, 41, 42: first and second conductive layers, 45: opening, 50: equal phase surface, 50N: normal vector, 50a, 50b: first and second equal phase surfaces, 50at, 50bt: first and second tangents, 60: analytical model, 60a, 60b: first and second analytical models, 91, 92: first and second electromagnetic waves, 91D: main radiation direction, 91P: projection direction, 91a: equal phase surface, 91z: direction, 92a: passing phase distribution, 110, 110a to 110e, 111, 112, 120 to 122: antenna device, 201: electric circuit, 210: radio device, AR1 to AR4: axial ratio, DD: filling factor, Dp1 to Dp4: first to fourth radiation section directions, Ds1, Ds2: 1st and 2nd slot direction, Dx1: 1st cross direction, Dz1: 1st axis direction, H1: thickness, HD: ratio, L1, L2: 1st and 2nd slot length, LD1, LD2: amount of change, OP: origin, PL1: 1st surface, SA: arrangement angle, S ρ : radial spacing, S φ: Circumferential spacing, W1, W2: 1st and 2nd span, Δφ: Angular difference, β0: Angular difference, β1~β4: 1st~4th angular difference, γ0: Other angular difference, γ1~γ4: 1st~4th other angular difference, δ1, δ2: 1st and 2nd span angle, δi1, δi2: 1st and 2nd angle, θ, θ0: Chilt angle, θ1, θ2: Angle, λ1, λ2: 1st and 2nd guided wave wavelength, ξ, ξ1: Wavelength ratio, ρ: Radial direction, φ: Azimuth angle, φ0: Angle, τ1, τ2: 1st and 2nd rotation angle, φ i : Equipotential surface angle, φ i1 φ iz Angle, φ t1 φ t2 : First and second wiring angles

Claims

1. a waveguide including a feed point and a first region; the first region is located around the feed point on a first plane intersecting a first axis direction passing through the feed point, the waveguide includes a plurality of radiating portions provided in the first region, each of the plurality of radiating portions includes a first slot extending along a first slot direction and a second slot extending along a second slot direction intersecting the first slot direction; the plurality of radiating portions include a first radiating portion and a second radiating portion, a first radiation portion direction from the feed point to the first radiation portion intersects with the first axis direction, a second radiation portion direction from the feed point to the second radiation portion intersects the first axis direction and intersects the first radiation portion direction, an antenna device, wherein a second absolute value of a second angular difference between the first slot direction in the second radiating portion and the second radiating portion direction is smaller than a first absolute value of a first angular difference between the first slot direction in the first radiating portion and the first radiating portion direction.

2. the plurality of radiating portions further include a third radiating portion, a third radiation portion direction from the feed point to the third radiation portion intersects the first axis direction and intersects the second radiation portion direction, the feed point is located between the third radiating portion and the first radiating portion in a direction along the first radiating portion direction, The antenna device according to claim 1 , wherein a third absolute value of a third angular difference between the first slot direction in the third radiating portion and the third radiating portion direction is greater than the second absolute value.

3. the plurality of radiating portions further include a fourth radiating portion, a fourth radiation portion direction from the feed point to the fourth radiation portion intersects the first axis direction and intersects the first radiation portion direction, the feed point is located between the fourth radiating portion and the second radiating portion in a direction along the second radiating portion direction, The antenna device according to claim 2 , wherein a fourth absolute value of a fourth angular difference between the first slot direction in the fourth radiating portion and the fourth radiating portion direction is greater than the first absolute value.

4. The antenna device according to claim 1 , wherein an angle between the first slot direction and the second slot direction is equal to or greater than 80° and equal to or less than 100°.

5. the first slot included in the first radiating portion has a first slot length along the first slot direction, the second slot included in the first radiating portion has a second slot length along the second slot direction, 2. The antenna device according to claim 1, wherein a ratio of an absolute value of a difference between the first slot length and the second slot length to the first slot length is 0.1 or less.

6. the first region includes a first partial region and a second partial region, the feeding point is located between the second partial region and the first partial region in a first intersecting direction intersecting with the first axis direction, the waveguide includes a first member; the first member includes a first member region corresponding to the first partial region and a second member region corresponding to the second partial region; the first member region and the second member region satisfy at least one of a first condition, a second condition, a third condition, a fourth condition, and a fifth condition; In the first condition, a first relative dielectric constant of the first member region is different from a second relative dielectric constant of the second member region, In the second condition, a density of the first holes included in the first component region is different from a density of the second holes included in the second component region, In the third condition, a first average size of the plurality of first holes included in the first component region is different from a second average size of the plurality of second holes included in the second component region; In the fourth condition, a first configuration of the first structure provided in the first component region is different from a second configuration of the second structure provided in the second component region, The antenna device according to any one of claims 1 to 5, wherein, in the fifth condition, the thickness of the first member included in the first member region is different from the thickness of the first member included in the second member region.

7. The waveguide is configured to guide a high-frequency signal supplied to the feed point, the first region includes a first partial region and a second partial region, the feeding point is located between the first partial region and the second partial region in a first intersecting direction intersecting with the first axial direction, 2. The antenna device according to claim 1, wherein a first guided wavelength in the waveguide in the first sub-region is shorter than a second guided wavelength in the waveguide in the second sub-region.

8. In each of the plurality of radiating portions, the first position is a position of the first slot on the waveguide; In each of the plurality of radiating portions, the second position is a position of the second slot on the waveguide; In each of the plurality of radiating portions, a first angle is an angle between an equiphase plane of the high-frequency signal propagating through the waveguide at the first position on the waveguide and the first slot direction, In each of the plurality of radiating portions, a second angle is an angle between the equiphase surface at the second position on the waveguide and the second slot direction, a first absolute angle value of the first angle at the first radiating portion is substantially equal to a second absolute angle value of the second angle at the first radiating portion; The antenna device according to claim 7 , wherein a third absolute angle value of the first angle in the second radiating portion is substantially the same as a fourth absolute angle value of the second angle in the second radiating portion.

9. the plurality of radiators are configured to radiate electromagnetic waves in response to the high-frequency signal; The antenna device according to claim 7 , wherein a projection direction of the main radiation direction of the electromagnetic wave onto the waveguide is along a direction from the second partial region to the first partial region.

10. the waveguide includes a first member; 10. The antenna device according to claim 9, wherein a first slow wave rate in the first partial region of the first member is different from a second slow wave rate in the second partial region of the first member.

11. The antenna device according to claim 10 , wherein the first member includes a dielectric material.

12. the first guided wavelength is a wavelength of the high-frequency signal propagating along a direction from the feed point to the first partial region, The antenna device according to claim 7 , wherein the second guided wavelength is a wavelength of the high frequency signal propagating along a direction from the feed point to the second partial region.

13. The radial spacing between the plurality of radiation portions arranged along a cross direction crossing the first axis direction is λ ０ / {1+sin(θ ０ )) is smaller than Said λ ０ is the wavelength of the high frequency signal in free space, Said θ ０ is an angle between the first axis direction and a main radiation direction of electromagnetic waves radiated from the plurality of radiating portions arranged along the intersecting direction that intersects with the first axis direction.

14. The circumferential spacing of the plurality of radiating portions in the circumferential direction around the first axial direction is ξλ ０ smaller than one of the plurality of radiating portions is adjacent to another of the plurality of radiating portions in the circumferential direction, a slow wave rate of the high frequency signal at the one of the plurality of radiating portions is equal to or greater than a slow wave rate of the high frequency signal at the other one of the plurality of radiating portions; ξ is the slow wave ratio of the high-frequency signal in the one of the plurality of radiating portions, Said λ ０ 8. The antenna device according to claim 7, wherein .lamda. is the wavelength of the high frequency signal in free space.

15. the first region includes a third partial region and a fourth partial region, the feed point is located between the third partial region and the fourth partial region, a direction from the power supply point to the third partial region intersects with a direction from the power supply point to the first partial region; a third guided wavelength in the waveguide in the third subregion is longer than the first guided wavelength and shorter than the second guided wavelength; The antenna device according to claim 7 , wherein a fourth guided wavelength in the waveguide in the fourth partial region is longer than the first guided wavelength and shorter than the second guided wavelength.

16. The antenna device according to claim 1 , wherein the plurality of radiating portions are configured to transmit and receive at least one of right-handed circularly polarized waves and left-handed circularly polarized waves.

17. The antenna device according to claim 1 , wherein the plurality of radiating portions are arranged substantially in a spiral shape or a concentric shape around the feed point.

18. Further comprising a first drive unit; the first drive unit is configured to rotate the waveguide in the first plane; The antenna device according to claim 1 , wherein the first electromagnetic waves radiated from the plurality of radiating portions are conically scanned by rotating the waveguide.

19. Further comprising a transparent member, the transmitting member is configured to transmit first electromagnetic waves radiated from the plurality of radiating portions, the transmitting member is configured to change a passing phase of the first electromagnetic wave, The antenna device according to claim 1 , wherein a direction of the second electromagnetic wave radiated from the transmitting member changes in accordance with the change in the passing phase.

20. Further comprising a second drive unit; the second drive unit is configured to rotate the transmission member, The antenna device according to claim 19 , wherein the direction of the second electromagnetic wave changes in response to a rotation of the transmitting member.

21. The antenna device according to claim 1; an electrical circuit coupleable to the feed point; A wireless device comprising:

Images