Ultra-wideband, low-distortion, omnidirectional, and placement-independent antenna

Abstract

The disclosed principle provides a novel antenna and a corresponding method for manufacturing the same. In one embodiment, the antenna according to the disclosed principle has a dielectric unit 200. The dielectric unit 200 may be azimuthally uniform, radially symmetric, or symmetric. The dielectric unit 200 may comprise a first conductive surface 120, a second conductive surface 140, and a non-conductive aperture surface 130. The first conductive surface 120 is located on a first radially inner surface of the dielectric unit 200 and may have both convex and concave surfaces. The second conductive surface 140 may be inclined with respect to the radial symmetry axis and may extend radially outward from the radial symmetry axis. The non-conductive aperture surface 130 may be located on the radially outer surface of the dielectric unit. The first conductive surface 120 and the second conductive surface 140 may define a dielectric mass 110 that extends radially toward the non-conductive aperture surface 130 and terminates at the non-conductive aperture surface 130.

Description

Technical Field

[0001] Cross - reference to Related Applications This application claims priority to U.S. Provisional Patent Application No. 63 / 421,508, filed Nov. 1, 2022; U.S. Provisional Patent Application No. 63 / 452,645, filed Mar. 16, 2023; and U.S. Provisional Patent Application No. 63 / 535,241, filed Aug. 29, 2023. Each of the above - mentioned U.S. Provisional Patent Applications is hereby incorporated by reference herein.

[0002] The present disclosure generally relates to wireless communication and, more particularly, to antenna technology.

Background Art

[0003] As the desired wireless data rate and bandwidth continue to increase, antenna performance often limits the performance of wireless systems. Recent wireless systems typically compensate for antenna limitations (such as distortion of wide - band signals) by hopping between a number of narrow frequency bands within a larger bandwidth. In this case, rather than transmitting and receiving instantaneously across the entire wide bandwidth, each frequency band (or channel) operates within a specific time window.

[0004] Conical antennas, such as discone and bi - cone antennas, have been used for omnidirectional wide - band operation. However, for wide bandwidths, the size of the conical antenna relative to the wavelength changes significantly, and thus pattern stability at wide bandwidths remains an issue. Therefore, wide - band conical antenna radiation patterns scan undesirable features in wireless communication (where an operator may wish to communicate point - to - point or broadcast) and signal intelligence applications (where an operator may wish to instantaneously observe signals arriving from all directions) over frequency.

[0005] Spherical or elliptical antennas have also been used for omnidirectional broadband operation, but they have the same beam scanning challenges as conical antennas. Furthermore, to achieve broadband, spherical or elliptical antennas are often made "relatively large in diameter," resulting in large lateral dimensions. Consequently, the dimensions of broadband spherical antennas exceed half a wavelength at higher frequencies, limiting their use in multi-antenna configurations such as antenna arrays. The large size of broadband antennas, especially those operating at low frequencies, also limits the use of broadband conical antennas in multi-antenna applications where wireless system performance is to be improved.

[0006] Conical, spherical, and elliptical antennas remain heavy, expensive, and difficult to manufacture and assemble in a variety of wireless applications. These antennas are affected by manufacturing tolerances and detuning issues near the feed point due to high electromagnetic field strength near the feed point. Conical, spherical, and elliptical antennas often involve placing a heavy conductive cone, sphere, or ellipsoid on the ground plane, or on top of another cone, sphere, or ellipsoid. This approach places a large, heavy radiating structure on a small feed pin, making it unsuitable for use in harsh environments.

[0007] Conical, spherical, or elliptical antennas also require a considerable ground plane to maintain matching at low operating frequencies. Otherwise, the antenna size becomes enormous at low frequencies. Operation without a large ground plane is susceptible to placement, and in this case, antenna placement, especially placing the antenna above or near a conductor, can excite undesirable operating modes, distort broadband signals, detune the antenna, and cause instability and unpredictability of the radiation pattern.

[0008] Broadband planar antennas, including those formed by combining conical and spherical antennas in a planar configuration, are subject to the limitations described above. Furthermore, planar antennas lack the durability required to operate in diverse environments, such as unmanned aerial systems where a highly durable structure is needed due to deployment, shock, and vibration. While planar antennas are easily integrated with planar transceiver circuits, many applications also require interface with coaxial connectors, resulting in a connector-to-board interface that is prone to failure in harsh environments.

[0009] In many cases, UWB antennas, which operate over wider bandwidths, transition undesirably between modes across the operating bandwidth, making them unsuitable for wireless applications requiring a stable phase center, low distortion, and controlled radiation pattern.

[0010] Due to the limitations summarized above, conventional UWB antennas cannot achieve the wide instantaneous bandwidth (IBW) and stable, controlled omnidirectional patterns desired in modern wireless applications. In wireless communication and signal intelligence applications, operators still cannot employ multiple antennas to cover the relevant bandwidth and instantaneously receive or identify wideband signals. [Overview of the project] [Problems that the invention aims to solve]

[0011] Therefore, there is a need for antennas that operate over a wide instantaneous bandwidth (IBW), particularly those that possess both a wide IBW and other desirable characteristics such as durability, small size and weight, unaffected by placement, omnidirectional radiation, and stable operation across frequencies. [Means for solving the problem]

[0012] According to one aspect of the present invention, an antenna having a dielectric unit is provided. The dielectric unit is azimuthally uniform, radially symmetric, or symmetric. The dielectric unit may comprise a first conductive surface, a second conductive surface, and a non-conductive aperture surface. The first conductive surface is located on a first radially inner surface of the dielectric unit and may have both convex and concave surfaces. The second conductive surface may be inclined with respect to the radial symmetry axis and extend radially outward from the radial symmetry axis. The non-conductive aperture surface may be located on the radially outer surface of the dielectric unit. The first and second conductive surfaces may define a dielectric volume that extends radially toward the non-conductive aperture surface and terminates at the non-conductive aperture surface.

[0013] In certain embodiments, the dielectric unit may be configured to instantaneously transmit and receive radio signals over a single instantaneous bandwidth of 10:1.

[0014] In certain embodiments, the dielectric unit may be configured to transmit and receive radio signals over an efficiency bandwidth of 10:1.

[0015] In certain embodiments, a dielectric unit may be configured to transmit and receive radio signals over a 10:1 bandwidth, wherein the 10:1 bandwidth comprises a plurality of instantaneous frequency bands, each of which has a bandwidth that is a multiple of the lowest operating frequency.

[0016] In certain embodiments, the maximum radius of the dielectric unit does not exceed one-tenth of the minimum operating wavelength at which the return loss of the antenna having the dielectric unit achieves or exceeds 6 dB.

[0017] In certain embodiments, the maximum height of the dielectric unit does not exceed one-sixth of the minimum operating wavelength at which the return loss of the antenna having the dielectric unit is achieved or exceeded by 6 dB.

[0018] In certain embodiments, the first conductive surface and the second conductive surface are arranged on a dielectric mass to form a dielectric unit as a single unit without a conducting volume.

[0019] In certain embodiments, the dielectric unit may be configured to prevent direct current flow between the first conductive surface and the second conductive surface.

[0020] In certain embodiments, the second conductive surface is located on the second radial inner surface of the dielectric unit and may be convex, concave, or both. In certain embodiments, the maximum radius of the second conductive surface exceeds the maximum radius of the first conductive surface. In certain embodiments, the maximum radius of the first conductive surface exceeds the maximum radius of the second conductive surface. In certain embodiments, the second conductive surface may be inclined with respect to the radial symmetry axis or the azimuthal plane.

[0021] In certain embodiments, the antenna may be coupled to a transmission line that can transmit signals to and receive signals from the antenna. In certain embodiments, the transmission line may be azimuthally uniform or radially symmetric.

[0022] According to one aspect of the present invention, an antenna having a dielectric unit is provided. The dielectric unit is azimuthally uniform, radially symmetric, or symmetric. The dielectric unit may comprise a first conductive surface, a second conductive surface, and a nonconductive aperture surface. The first conductive surface is located on a first radially inner surface of the dielectric unit and may be convex, concave, or both. The second conductive surface may be inclined with respect to the radial symmetry axis and extend radially outward from the radial symmetry axis. The nonconductive aperture surface may be located on the radially outer surface of the dielectric unit. The first and second conductive surfaces may define a dielectric mass that extends radially toward and terminates at the nonconductive aperture surface.

[0023] In certain embodiments, the second conductive surface is located on the second radial inner surface of the dielectric unit and may have a convex, concave, or both.

[0024] In certain embodiments, the antenna may be coupled to a ground plane defining a radiation horizon or azimuthal plane. In certain embodiments, the radiation horizon or azimuthal plane may be perpendicular to the axis of radiation symmetry. In certain embodiments, the radiation horizon or azimuthal plane may be inclined with respect to the axis of radiation symmetry.

[0025] In certain embodiments, the antenna may be coupled to a transmission line that can transmit signals to and receive signals from a dielectric unit.

[0026] In certain embodiments, a dielectric mass may have one or more dielectric surfaces. In certain embodiments, a dielectric mass may have a first dielectric surface on a first radial inner surface. In certain embodiments, a dielectric mass may have a second dielectric surface on a second radial inner surface. In certain embodiments, one or more conductive surfaces may be arranged on one or more dielectric surfaces of the dielectric mass to form a dielectric unit.

[0027] In certain embodiments, a dielectric unit or antenna may be configured to radiate a pattern using a beam that is substantially uniform in azimuthal and includes a radiation horizon. In certain embodiments, a dielectric unit or antenna may be configured to radiate a pattern using a beam that is substantially uniform in azimuthal and includes a radiation horizon over a 4:1, 6:1, or 8:1 pattern bandwidth. In certain embodiments, a dielectric unit or antenna may be configured to radiate a pattern using a conical beam substantially aligned with the radiation axis of symmetry and a beam that is substantially uniform in azimuthal and includes a radiation horizon. In certain embodiments, a dielectric unit or antenna may be configured to radiate a pattern using a conical beam substantially aligned with the radiation axis of symmetry and a beam that is substantially uniform in azimuthal and includes a radiation horizon over a 4:1 or 6:1 pattern bandwidth.

[0028] In certain embodiments, a symmetric dielectric unit or antenna may have a major axis defining the maximum radial dimension of the dielectric unit or antenna. In certain embodiments, a symmetric dielectric unit or antenna may have a minor axis defining the minimum radial dimension on the radial outer surface of the dielectric unit or antenna.

[0029] In certain embodiments, the ratio of the semi-major axis to the minor axis is in the range of 1.25 to 2.5.

[0030] In certain embodiments, the dielectric unit or antenna may be configured to preferentially transmit and receive radio signals in the short radiation axis direction. In certain embodiments, the dielectric unit or antenna may be configured to preferentially transmit and receive radio signals in the long radiation axis direction. In certain embodiments, the dielectric unit or antenna may be configured to preferentially transmit and receive radio signals in a conical beam azimuthally aligned with the long radiation axis.

[0031] In certain embodiments, the antenna or dielectric unit may be configured based on the signal type of the radio signal transmitted or received by the dielectric unit or antenna. In certain embodiments, the positions of the first conductive surface, the second conductive surface, or the non-conductive aperture surface may be based on the signal type of the radio signal transmitted or received by the dielectric unit. In certain embodiments, the signal type may consist of white Gaussian noise. In certain embodiments, the signal type may include a chirp spread spectrum signal. In certain embodiments, the signal type may include a direct sequence spread spectrum signal. In certain embodiments, the signal type may include a featureless spread spectrum signal.

[0032] According to one aspect of the present invention, a system is provided comprising an antenna, a transmitting channel, and a receiving channel. The antenna may be configured to transmit and receive radio signals over one or more instantaneous bandwidths, each including up to 3.2 GHz. The antenna may be configured to transmit and receive radio signals over one or more instantaneous bandwidths, each including at least 3.2 GHz. The antenna may be configured to transmit and receive radio signals over one or more instantaneous bandwidths, each including up to 6.4 GHz. The antenna may be configured to transmit and receive radio signals over one or more instantaneous bandwidths, each including at least 6.4 GHz.

[0033] A transmit channel may be configured to be coupled to an antenna and instantaneously transmit a first signal in a transmit frequency band having an instantaneous bandwidth of at least 3.2 GHz. A receive channel may be configured to be coupled to an antenna and instantaneously receive a second signal in a receive frequency band having an instantaneous bandwidth of at least 3.2 GHz. A transmit channel may be configured to be coupled to an antenna and instantaneously transmit a first signal in a transmit frequency band having an instantaneous bandwidth of up to 3.2 GHz. A receive channel may be configured to be coupled to an antenna and instantaneously receive a second signal in a receive frequency band having an instantaneous bandwidth of up to 3.2 GHz.

[0034] A transmit channel may be configured to be coupled to an antenna and instantaneously transmit a first signal in a transmit frequency band having an instantaneous bandwidth of at least 6.4 GHz. A receive channel may be configured to be coupled to an antenna and instantaneously receive a second signal in a receive frequency band having an instantaneous bandwidth of at least 6.4 GHz. A transmit channel may be configured to be coupled to an antenna and instantaneously transmit a first signal in a transmit frequency band having an instantaneous bandwidth of up to 6.4 GHz. A receive channel may be configured to be coupled to an antenna and instantaneously receive a second signal in a receive frequency band having an instantaneous bandwidth of up to 6.4 GHz.

[0035] In certain embodiments, the transmit frequency band does not overlap with the receive frequency band in terms of frequency. In certain embodiments, the transmit channel and the receive channel may be separated on the basis that the transmit frequency band does not overlap with the receive frequency band. In certain embodiments, the transmit frequency band may be higher in terms of frequency than the receive frequency band. In certain embodiments, the transmit channel may be configured for RF upconversion of a first signal. In certain embodiments, the receive channel may be configured for direct digital downconversion of a second signal. In certain embodiments, the receive frequency band may be higher in terms of frequency than the transmit frequency band. In certain embodiments, the receive channel may be configured for RF downconversion of a second signal. In certain embodiments, the transmit channel may be configured for direct digital upconversion of a first signal.

[0036] In certain embodiments, the transmit channel and the receive channel are configured for spread spectrum communication. In certain embodiments, the first signal may include a first spreading code, and the second signal may include a second spreading code. In certain embodiments, the transmit channel and the receive channel may be separated based on the fact that the first spreading code and the second spreading code are different codes. In certain embodiments, the transmit channel and the receive channel may be separated based on the fact that the first spreading code and the second spreading code are uncorrelated.

[0037] In certain embodiments, the transmit channel and the receive channel may be configured for half-duplex communication.

[0038] According to one aspect of the present invention, a method is provided comprising one or more steps of forming a dielectric unit. The steps for forming the dielectric unit may include arranging a first conductive surface on a first radial inner surface of a dielectric mass and arranging a second conductive surface on a second radial inner surface of the dielectric mass. In certain embodiments, the dielectric mass, the first conductive surface, and the second conductive surface form a dielectric unit without the conductive mass.

[0039] According to one aspect of the present invention, a method is provided comprising one or more steps, including forming a dielectric mass. In a particular embodiment, the dielectric mass may have a first radial inner surface, a second radial inner surface, and a non-conductive opening surface on the radial outer surface of the dielectric mass. The first radial inner surface may be convex, concave, or both. The second radial inner surface may be inclined with respect to the radial symmetry axis and extend radially outward from the radial symmetry axis. Additional steps may include arranging a first conductive surface on the first radial inner surface of the dielectric mass and arranging a second conductive surface on the second radial inner surface of the dielectric mass.

[0040] According to one aspect of the present invention, a method is provided comprising one or more steps of forming an antenna. The steps of forming the antenna may include fitting a first conductive surface of a first radiator onto a first radial inner surface of a dielectric mass, and fitting a second conductive surface of a second radiator onto a second radial inner surface of the dielectric mass. The first conductive surface and the second conductive surface may define a dielectric mass that extends radially toward and terminates at a non-conductive aperture.

[0041] In certain embodiments, the first conductive surface may be convex, concave, or both. In certain embodiments, the second conductive surface may be convex, concave, or both. In certain embodiments, the second conductive surface may be inclined with respect to the radial symmetry axis and extend radially and longitudinally outward from the radial symmetry axis.

[0042] In certain embodiments, the first radiator may be integrated into a conductive top hat. In certain embodiments, the second radiator may be integrated into a conductive ground plane.

[0043] In certain embodiments, the first radiator may be formed without a conductive mass. In certain embodiments, the first radiator may be formed by arranging a first conductive surface on a first dielectric base. In certain embodiments, the second radiator may be formed without a conductive mass. In certain embodiments, the second radiator may be formed by arranging a second conductive surface on a second dielectric base. In certain embodiments, the first dielectric base and the dielectric mass may be composed of different dielectric materials. In certain embodiments, the second dielectric base and the dielectric mass may be composed of different dielectric materials.

[0044] In certain embodiments, a top hat may be fitted to a dielectric mass. In certain embodiments, the top hat may secure a first radiator to the dielectric mass. In certain embodiments, the dielectric mass may have one or more lips for fitting to a top hat. In certain embodiments, the top hat may be fitted to the lips of the dielectric mass. In certain embodiments, the dielectric mass may have an integrated rim for securing a first radiator. In certain embodiments, the maximum radius of the first radiator may exceed the minimum radius of the integrated rim. In certain embodiments, the top hat may be fitted to the integrated rim of the dielectric mass. In certain embodiments, the first radiator may be inserted through an opening in the dielectric mass. In certain embodiments, the maximum radius of the first radiator may exceed the maximum radius of the opening in the dielectric mass.

[0045] In certain embodiments, the first radiator, the second radiator, and the dielectric mass may be assembled such that the dielectric mass partially or completely extends longitudinally between the first and second radiators and partially or completely fixes the first and second radiators. In certain embodiments, the dielectric mass may extend longitudinally beyond the first radiator and fix the first radiator.

[0046] Embodiments herein further include corresponding systems, apparatus, and computer program products, as well as methods for manufacturing them. Accordingly, embodiments herein generally include methods for fabricating and operating antennas that are small in size and weight, ultra-wideband, low-distortion, omnidirectional, and unaffected by placement, and methods for improving the performance of wireless systems based on these characteristics.

[0047] The technical advantages of certain embodiments may include instantaneous transmission and reception of broadband radio signals, consistent antenna operation across wide bandwidths and installation environments, small weight and size antennas, wide pattern bandwidths, and low-cost production of highly durable antennas. Other technical advantages should be readily apparent to those skilled in the art from the description and drawings herein. While specific advantages have been described so far, various embodiments may include all or some of these advantages, or none of them.

[0048] Herein, in order to fully understand this disclosure and its merits, please refer to the following description, which should be read in conjunction with the attached drawings. [Brief explanation of the drawing]

[0049] [Figure 1] This figure shows the geometric shape and characteristics of an exemplary dielectric mass according to a specific embodiment. [Figure 2A] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 2B] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 3A] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 3B] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 3C] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 3D] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 3E] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 3F] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 4A] This figure shows the wireless performance of an exemplary antenna in terms of time-domain performance according to a specific embodiment. [Figure 4B] This figure shows the wireless performance of an exemplary antenna in terms of time-domain performance according to a specific embodiment. [Figure 4C] This figure shows the wireless performance of an exemplary antenna with respect to return loss according to a specific embodiment. [Figure 4D] This figure shows the wireless performance of an exemplary antenna with respect to return loss according to a specific embodiment. [Figure 5A] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 5B] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 6A] This figure shows the wireless performance of an exemplary antenna with respect to return loss according to a specific embodiment. [Figure 6B] This figure shows the wireless performance of an exemplary antenna with respect to return loss according to a specific embodiment. [Figure 6C] This figure shows the wireless performance of an exemplary antenna in terms of time-domain performance according to a specific embodiment. [Figure 7A] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 7B] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 7C] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 7D] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 7E] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 7F] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 8A] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 8B] This figure shows the wireless performance of an exemplary antenna with respect to return loss according to a specific embodiment. [Figure 9A] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 9B] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 9C] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 9D] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 9E] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 9F] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 10A] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 10B] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 11A] This figure shows the wireless performance of an exemplary antenna with respect to return loss according to a specific embodiment. [Figure 11B]This figure shows the wireless performance of an exemplary antenna in terms of time-domain performance according to a specific embodiment. [Figure 11C] This figure shows the wireless performance of an exemplary antenna in terms of time-domain performance according to a specific embodiment. [Figure 12A] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 12B] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 12C] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 12D] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 12E] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 12F] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 12G] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 12H] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 13A] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 13B] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 13C] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 14A] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 14B] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 14C] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 14D] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 15] This figure illustrates the wireless performance of an exemplary antenna according to a specific embodiment, with respect to return loss performance. [Figure 16A] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 16B] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 16C] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 17A] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 17B] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 17C] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 17D] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 18] This figure shows the wireless performance of an exemplary antenna with respect to return loss according to a specific embodiment. [Figure 19A] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 19B] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 19C] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 20A] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 20B] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 20C] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 20D] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 21] This figure illustrates the wireless performance of an exemplary antenna according to a specific embodiment, with respect to return loss performance. [Figure 22] This figure shows an exemplary spectrum assignment for one or more radio signals transmitted and received by an antenna disclosed herein, according to a particular embodiment. [Figure 23] This figure shows an exemplary transceiver system according to a specific embodiment. [Figure 24] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 25A] This figure shows an exemplary top-hat topology in an antenna according to a specific embodiment. [Figure 25B] This figure shows an exemplary top-hat topology in an antenna according to a specific embodiment. [Figure 25C] This figure shows an exemplary top-hat topology in an antenna according to a specific embodiment. [Figure 26A] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 26B] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 27A] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 27B] This figure shows the geometric shape and features of an exemplary antenna according to a specific embodiment. [Figure 28A]This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 28B] This figure illustrates the radio performance of an exemplary antenna with respect to its radiation pattern, according to a specific embodiment. [Figure 29] This is a flowchart illustrating an exemplary method for forming a dielectric unit according to a specific embodiment. [Figure 30] This is a flowchart illustrating an exemplary method for coupling dielectric units to a transmission line and a ground plane according to a specific embodiment. [Figure 31] This is a flowchart illustrating an exemplary method for forming an antenna comprising a dielectric block, a first radiator, and a second radiator, according to a particular embodiment. [Figure 32] This is a flowchart illustrating an exemplary method for forming an antenna comprising a dielectric block, a first radiator, a second radiator, and a top hat, according to a particular embodiment. [Modes for carrying out the invention]

[0050] As discussed above, an antenna capable of transmitting and receiving signals over a wide instantaneous bandwidth (IBW) is required. A wide IBW is an IBW over which the antenna can operate with acceptable distortion performance at any given moment (or, substantially, over a time span corresponding to a time-domain signal transmitted over the IBW). To transmit and receive signals instantaneously, the antenna must be able to transmit and receive signals with high fidelity over the entire bandwidth of the signal without dividing the signal into small bandwidths or hopping between frequency bands in different time windows. To obtain a large IBW, the antenna must transmit and receive the transmitted or received signal over its bandwidth with substantially no distortion. Distortion can be caused by dispersion, reflection, and excitation of undesirable modes that absorb signal energy from the desired transmit channel.

[0051] The fidelity factor is a metric used to evaluate the fidelity, and even the distortion, of a transmitted or received signal. An antenna with a high fidelity factor across a frequency bandwidth (e.g., 2:1) may have the same IBW (e.g., 2:1), but it may have a larger frequency bandwidth (e.g., 3:1) in a way that prevents it from instantaneously transmitting and receiving across that bandwidth. For example, an antenna may be matched across a frequency bandwidth of 200–600 MHz (e.g., to 50 ohms), but it will only transmit or receive signals on a 20 MHz channel because it distorts the signal in a wider bandwidth. Low fidelity (high distortion) limits the ability of a receiver to receive (acquire, synchronize, and track) the signal.

[0052] Antennas with high transmission phase linearity (S21 phase linearity) maintain higher fidelity, and maintaining phase linearity becomes more difficult as bandwidth increases. Similarly, to maintain high fidelity, a smooth and slowly changing transmission amplitude is desirable. 1 Excitation of multiple modes can lead to phase nonlinearity and discontinuities in transmission amplitude. Therefore, the embodiments disclosed herein seek to minimize transmission phase nonlinearity and the excitation of undesirable modes in order to obtain high fidelity. 1 Because dispersion effects and undesirable mode behaviors that limit fidelity are typically more discernible in phase than in amplitude, this disclosure focuses on transmission phase linearity as an indicator of high fidelity. However, it should be understood that in embodiments of this specification having high fidelity, both sufficiently linear transmission phase and slowly changing transmission amplitude are obtained to achieve the fidelity disclosed.

[0053] As used herein, the term “minimum operating frequency” refers to the lowest frequency at which the antenna’s return loss is achieved or exceeds 10 dB, unless otherwise indicated. In certain embodiments, the term “minimum operating frequency” may refer to the lowest frequency at which the antenna’s return loss is achieved or exceeds 6 dB, as indicated by its radio performance. In this disclosure, the variable fL is used as a normalized frequency variable that may or may not correspond to the minimum operating frequency in any particular embodiment. For example, fL is the minimum operating frequency for antenna 1300 (Figure 13), antenna 1600 (Figure 16), and antenna 1900 (Figure 19), as indicated by the return loss performance of each antenna. The minimum operating frequency corresponds to the minimum operating wavelength λ = c / f. Similarly, the term “maximum operating frequency” refers to the highest frequency at which the antenna’s efficiency bandwidth, IBW, and pattern bandwidth overlap. In many embodiments, the maximum operating frequency is 6 fL or 12 fL and is limited by the efficiency bandwidth or pattern bandwidth. Those skilled in the art will understand that the minimum operating wavelength or maximum operating frequency, or alternative definitions thereof (e.g., a return loss of 6 dB or a return loss of 10 dB), can be determined simply by renormalizing the parameters defined based on the minimum operating wavelength or maximum operating wavelength, or the minimum operating frequency or maximum operating frequency.

[0054] The antenna embodiments described herein include a dielectric block. Figure 1 shows a cross-sectional view of the geometric shape and features of an exemplary dielectric block 110. The dielectric block 110 may have a plurality of surfaces, including a first radial inner surface 120, a non-conductive aperture surface 130, an inner ground surface 140, edges 150A, 150B, and a base 160. The dielectric block 110 can be fitted into a transmission line dielectric 170.

[0055] To facilitate reference to various physical and radio performance characteristics (especially radiation patterns), Figure 1 also shows the azimuthal plane 180, the radiation symmetry axis 190 located at the radiation center of antenna 100, and the XYZ coordinate system. Throughout this disclosure, antenna performance characteristics (e.g., radiation patterns) and physical characteristics are described with reference to a spherical coordinate system (θ,φ,r), a Cartesian coordinate system (X,Y,Z), or a cylindrical coordinate system (ρ,φ,Z) as appropriate. As used herein, longitudinal dimensions or distances refer to the Z dimension, and radial dimensions or distances refer to the ρ, X, or Y dimension.

[0056] As shown in Figure 1, the dielectric mass 110 is azimuthally uniform (without variation according to φ), as can be seen when a cross-section is taken in an arbitrary elevation plane (θ-r plane) to obtain the diagram in Figure 1. When the cross-sectional view in Figure 1 is rotated about the radial symmetry axis 190, a three-dimensional dielectric mass 110 is obtained in which each face in the three-dimensional view has multiple surfaces corresponding to the curve in the cross-sectional view in Figure 1. The dielectric mass 110 can be radially symmetric or azimuthally uniform with respect to the radial symmetry axis 190. The dielectric mass 110 terminates radially inward at the first radial inner surface 120. The dielectric mass 110 terminates radially outward at the non-conductive opening surface 130. The dielectric mass 110 terminates at the longitudinal maximum of one or more edges 150A. Figure 1 shows one edge 150A at the longitudinal maximum of the dielectric mass 110. The dielectric mass 110 terminates at the longitudinal minimum of the base 160. The dielectric mass 110 also has an inner ground surface 140 extending radially outward from the base 160 to one or more edges 150B or nonconductive opening surface 130. Figure 1 shows one edge 150B between the inner ground surface 140 and the nonconductive opening surface 130.

[0057] In certain embodiments, the dielectric mass 110 has a maximum radius determined by the maximum radial dimension of the non-conductive opening surface 130. In certain embodiments, the dielectric mass 110 has a maximum height determined by the longitudinal distance from the base 160 to the longest longitudinal portion of the dielectric mass 110.

[0058] A first radial inner surface 120 located on the radially inward side of the dielectric mass 110 may extend longitudinally from the base 160 to the longest longitudinal portion of the dielectric mass 110 (edge ​​150A in Figure 1). In certain embodiments, the first radial inner surface 120 includes a convex surface, a concave surface, or both convex and concave surfaces. In certain embodiments, the space on the radially inward side of the first radial inner surface 120 is a cavity (e.g., free space or air). As will be discussed further below, in certain embodiments, a conductive surface (e.g., a metallic radiator) or a dielectric structure (e.g., a dielectric base) may be inserted into the cavity. In certain embodiments, the conductive surface may be fitted into the first radial inner surface 120 when fabricating an antenna.

[0059] The nonconductive aperture surface 130, located on the radially outer surface of the dielectric mass 110, determines the radial maximum portion of the dielectric mass 110. As shown in Figure 1, the nonconductive aperture surface 130 extends longitudinally between two edges 150A and 150B. In certain embodiments, the nonconductive aperture surface 130 may extend longitudinally from the inner ground surface 140 to one or more edges 150A at the longitudinal maximum portion of the dielectric mass 110. The dielectric mass 110 terminates at the nonconductive aperture surface 130 in free space. In certain embodiments, the nonconductive aperture surface 130 may be convex, concave, or both convex and concave.

[0060] As shown in Figure 1, the inner ground surface 140 extends radially outward from the base 160 to one or more edges 150B. In certain embodiments, the inner ground surface 140 may extend radially outward from the base 160 to the nonconductive opening surface 130. In certain embodiments, the inner ground surface 140 may extend to the minimum longitudinal portion of the dielectric mass 110. Although not shown in Figure 1, in certain embodiments, the inner ground surface 140 may extend to the outer diameter of the transmission line dielectric 170. In certain embodiments, the inner ground surface 140 may include a convex surface, a concave surface, or both convex and concave surfaces.

[0061] The dielectric mass 110 may include one or more edges 150A, 150B. As shown in Figure 1, the dielectric mass 110 includes one edge 150A at the maximum longitudinal portion of the dielectric mass 110 and one edge 150B between the inner ground surface 140 and the nonconductive opening surface 130. In certain embodiments, the edges 150A, 150B may be included in the dielectric mass 110 to accommodate manufacturing tolerances or to provide a flat surface (e.g., a flat surface parallel to the XY plane) for mating with other structures, as will be discussed further below. In certain embodiments, the dielectric mass 110 may not include edge 150A or edge 150B.

[0062] As shown in Figure 1, the base 160 is located at the minimum longitudinal portion of the dielectric mass 110. In certain embodiments, the base 160 may be placed on or parallel to the azimuthal plane 180. In certain embodiments, the base 160 may extend to the maximum radial portion of the transmission line dielectric 170. As shown in Figure 1, the base 160 extends beyond the maximum radius of the transmission line dielectric 170, which may have the advantage of stabilizing the dielectric mass 110 or providing a flat surface for mating with an external structure (e.g., an external ground plane).

[0063] The transmission line dielectric 170 can be any dielectric or dielectric composition in the transmission line coupled to the dielectric mass 110. As shown in Figure 1, the transmission line dielectric 170 is an insulating jacket that separates the inner conductor and the outer conductor in a coaxial transmission line. In certain embodiments, the transmission line dielectric 170 may be azimuthally uniform or radially symmetric.

[0064] As shown in Figure 1, the azimuth plane 180 defines the radial horizon (θ=90°). In certain embodiments, the azimuth plane 180 may also define an azimuth plane (θ=90°, XY) corresponding to the external ground plane.

[0065] The radial symmetry axis 190 defines the Z-axis, and with respect to the Z-axis, the dielectric mass 110 is azimuthally uniform or radially symmetric. An azimuthally uniform structure does not change with respect to the azimuthal angle (φ). The dielectric mass 110 is azimuthally uniform as shown in Figure 1. In certain embodiments, the dielectric mass 110 may be radially symmetric to achieve specific high-frequency (RF) performance characteristics or to facilitate a specific manufacturing method.

[0066] All structures shown in Figure 1 (dielectric mass 110 and transmission line dielectric 170) are composed of dielectric materials. In certain embodiments, the dielectric mass may be formed from one or more dielectric materials, including polycarbonate, polytetrafluoroethylene (PTFE), nylon, polyethylene terephthalate glycol (PETG), polyetherimide (PEI), ABS, polyurethane foam, polyethylene foam, polystyrene foam, polymethacrylimide foam, ceramic-filled resin, or polymer-filled resin. The dielectric mass 110 may be translucent or transparent. The transmission line dielectric 170 may be formed from any suitable dielectric material or composition of materials, including the materials described above, for transmitting RF energy to the dielectric mass 110. 2 For example, the transmission line dielectric 170 may be composed of Teflon® or Ultem® material, which are commonly used in coaxial transmission lines. 2 All antennas in this specification are matched to a 50Ω transmission line. Those skilled in the art will understand that the antenna embodiments disclosed herein can be matched to impedances greater than 50Ω without impairing performance.

[0067] As shown in Figure 1, the dielectric mass 110 is composed of a single, uniform dielectric material. In certain embodiments, the dielectric mass may include one or more cavities that do not contain dielectric material. For example, certain spaces in the dielectric mass may be formed by additive manufacturing, while other spaces are left as cavities during the additive manufacturing process. In certain embodiments, the dielectric mass may include one or more drainage holes to empty or backfill one or more cavities. In certain embodiments, one or more drainage holes may be radially symmetric, azimuthally uniform, or symmetric. For example, to maintain the structural integrity of the dielectric mass, N drainage holes, each separated by 360 / N degrees azimuthal, may help empty N separate cavities. In certain embodiments, the inclusion of one or more cavities in the dielectric mass does not affect the continuity of conductive surfaces in the dielectric mass. For example, the dielectric unit may include one or more cavities and drainage holes that do not intersect with the first radial inner surface 120, the inner ground surface 140, or any other surface that may form a base for conductive surfaces.

[0068] In certain embodiments, the dielectric mass may be composed of multiple dielectric materials. For example, one or more cavities may be filled with dielectric material. Including one or more cavities in the dielectric mass can reduce weight, control the effective dielectric constant of the antenna, and suppress or promote radiation in different modes. In certain embodiments, the effective dielectric constant may be calculated as the volume-weighted average of the dielectric constants of one or more materials in the dielectric mass. For example, a dielectric mass formed from a material having a dielectric constant of 2.1 and having air cavities (dk=1) in 50% of its volume has an effective dielectric constant dk e =(0.5)(2.1)+(0.5)(1)=1.55. In certain embodiments, one or more cavities may facilitate certain features in the antenna radiation pattern, such as radially symmetric, azimuthally uniform, or symmetric, with an azimuthally uniform beam, or greater directivity in a particular direction.

[0069] In certain embodiments, the dielectric mass may be formed from a material having a dielectric constant of 2.0 to 3.6. In certain embodiments, the dielectric unit may have an effective dielectric constant of 1.4 to 3.6. In certain embodiments, to improve structural integrity, the dielectric unit may have an effective dielectric constant of 1.8 to 3.1.

[0070] In certain embodiments, the dielectric mass may be formed from a material having a specific gravity of 1.02 to 1.38. In certain embodiments, the dielectric mass may be formed from a plurality of materials, including a first material having a specific gravity of 1.02 to 1.38 and a second material having a specific gravity of 0.03 to 0.2.

[0071] In certain embodiments, a dielectric unit may be formed from a dielectric mass 110. To form the dielectric unit, a first conductive surface may be positioned on a first radial inner surface 120, and a second conductive surface may be positioned on an inner ground surface 140. In certain embodiments, the first or second conductive surface may also be positioned on one or more edges 150A, 150B. The second conductive surface may also be positioned on a base 160 on the radially outer side of the transmission line dielectric 170. In certain embodiments, forming a dielectric mass (and dielectric unit) as a single, integrated whole enables previously unattainable dielectric compositions and effective RF characteristics for achieving the radio performance disclosed herein.

[0072] The dielectric block 110 is fitted into the transmission line dielectric 170 in Figure 1. In a particular embodiment, the transmission line dielectric 170 couples RF energy to the dielectric block 110 (transmits it into free space), or the dielectric block 110 couples RF energy to the transmission line 170 (receives it from free space).

[0073] The dielectric mass 110 can be formed by additive manufacturing, machining, injection molding, or similar processes. For example, the dielectric mass 110 can be formed from Ultem® material in a fused deposition modeling (FDM) process. As another example, the dielectric mass 110 can be formed from ABS in a stereolithography (SLA) process. As yet another example, the dielectric mass 110 can be formed by machining Teflon.

[0074] The surface of the dielectric mass 110 may be epoxy coated, painted, or treated for various applications. In certain embodiments, the non-conductive aperture surface 130 may be painted. For example, the non-conductive aperture surface 130 may be painted white, light blue, gray, or a combination of colors to make the antenna less visible on an aerial or sea platform. In certain embodiments, the surface of the dielectric mass 110 may be treated to reduce the adhesion of water, dirt, or other substances that may affect structural integrity, service life, or radio performance. In certain embodiments, the surface of the dielectric mass 110 may be treated to facilitate the fabrication of the antenna. For example, the first radial inner surface 120 may be sandblasted or chemically etched to promote adhesion of the first conductive surface to the first radial inner surface 120.

[0075] Figure 2 shows the overall geometric shape and features of antenna 200 in a cross-sectional view (Figure 2A) and a perspective view (Figure 2B). Figure 2A shows a cross-section of antenna 200 in the ZY plane, while any cross-sectional section of Figure 2B in the elevation plane (θ-r) yields the cross-sectional view of Figure 2A. As shown, antenna 200 comprises a dielectric mass (e.g., dielectric mass 110 shown in Figure 1), a first radiator 205, an inner ground 210, and an outer ground 220. Antenna 200 can be coupled to a transmission line 230 for the transmission and reception of RF / radio signals.

[0076] As shown in Figures 2A and 2B, the maximum radius of antenna 200 is λ L The maximum height of the antenna 200 is λ, and it does not exceed / 12. LIt shall not exceed / 5. In certain embodiments, the maximum antenna height may be increased to shift the antenna's operating bandwidth to lower frequencies or to improve return loss at lower frequencies in the antenna's operating bandwidth. In certain embodiments, lowering the antenna height may improve transmission phase linearity across the antenna's operating bandwidth, thereby reducing distortion and increasing the fidelity of instantaneous broadband radio signals. In certain embodiments, the antenna radius may be adjusted to facilitate matching with the antenna or to achieve the antenna gain at a desired frequency.

[0077] When used to form the antenna 200, the dielectric block 110 may be formed from any fabrication process, material, or composition of material described with respect to Figure 1.

[0078] As shown in Figures 2A and 2B, the first radiator 205 is located radially inward of the dielectric mass 110 and presents a conductive surface to the first radial inner surface 120. The first radiator 205 may extend longitudinally from the base 160 to the maximum longitudinal portion of the dielectric mass 110 (edge ​​150A in Figure 1). In certain embodiments, the first radiator 205 may extend from the central conductor of the transmission line (e.g., a pin extending from the transmission line) to the maximum longitudinal portion 150A of the dielectric mass 110. The first radiator 205 may be azimuthally uniform or radially symmetric. The first radiator 205 may extend radially from the inner conductor of the transmission line to one or more edges 150A of the dielectric mass 110. In certain embodiments, the first radiator 205 may extend to the maximum longitudinal radius of the dielectric mass 110. In certain embodiments, the first radiator 205 includes a convex surface, a concave surface, or both a convex and a concave surface.

[0079] In certain embodiments, the space on the radially inner side of the first radiator 205 is a cavity (e.g., free space or air). In certain embodiments, a dielectric structure (e.g., a dielectric filler) may be inserted into the cavity on the radially inner side of the first radiator 205.

[0080] The first radiator 205 may be formed by machining, additive manufacturing, sintering, stamping, spraying, rolling, or deposition processes, or by one or more similar processes. For example, the first radiator 205 may be machined or additive manufactured from a conductive material (e.g., copper or aluminum) such that the first radiator 205 fills the entire space on the radially inward side of the first radial inner surface 120. As another example, the first radiator 205 may be formed without a conductive mass by depositing a first conductive surface on the first radial inner surface 120. As yet another example, the first radiator 205 may be formed without a conductive mass by stamping a conductive sheet and bonding it to the first radial inner surface 120.

[0081] In certain embodiments, forming the first radiator 205 without a conductive mass may have the advantage of reducing the size and weight of the antenna 200. As used herein, the term “without a conductive mass” means that the conductor in the antenna or dielectric unit, such as the first or second conductive surface, is thin enough that the mass of the conductor does not substantially affect the RF performance (e.g., the conductor may be modeled or analyzed as a surface) or the weight of the antenna. For example, a conductive surface may be without a conductive mass if its thickness is less than 1 / 100 of the highest operating wavelength. In certain embodiments, a conductive surface may be without a conductive mass if its thickness is less than 1 / 50 of the highest operating wavelength. In certain embodiments, one or more conductive surfaces may have a thickness of at least 10 degrees of penetration at the lowest operating frequency to minimize RF loss.

[0082] In certain embodiments, the first radiator 205 may be formed from a conductive mass to partially fill a cavity on the radially inward side of the first radial inner surface 120. For example, the first radiator 205 may be formed by stamping a conductive plate or by additively manufacturing a conductive material to a certain thickness and bonding it to the first radial inner surface 120. Forming the first radiator 205 to partially fill a cavity on the radially inward side of the first radial inner surface 120 may have the advantage of presenting a conductive surface in the maximum longitudinal dimension of the antenna 200 for mating or coupling to other structures. For example, the first radiator 205 may be formed with a radial thickness sufficient to facilitate conductive epoxy resin bonding or other bonding of a conductive top hat to the first radiator 205. In another embodiment, the conductive top hat may be bonded to the first radiator 205 via one or more edges 150A. Coupling a metal top hat to the first radiator 205 may have the advantage of isolating any cavities radially inside the first radiator 205 from the external environment and preventing current from flowing radially inside the first radiator 205.

[0083] In certain embodiments, the first radiator 205 may be formed by arranging one or more conductive surfaces on a dielectric substrate. For example, the first radiator 205 may be formed without a conductive mass by electrolessly depositing copper onto the dielectric substrate. As another example, the first radiator 205 may be formed by stamping one or more conductive sheets and fitting the stamped sheets onto the dielectric substrate. Forming the first radiator 205 by arranging conductive surfaces on a dielectric substrate may have one or more advantages, including reducing the size and weight of the antenna, enhancing the structural integrity of the first radiator 205, reducing RF loss by presenting a smooth conductive surface to the associated RF energy passing through the dielectric mass, and facilitating a non-selective process for presenting a conductive surface on the first radial inner surface 120. For example, forming the first radiator 205 on a dielectric substrate may allow electroplating of the entire surface on the dielectric substrate without masking. The dielectric base in the first radiator 205 may consist of any dielectric material discussed with respect to the dielectric mass 110, or any dielectric material suitable for mating, depositing, and bonding a conductive surface onto the dielectric base.

[0084] In certain embodiments, the first radiator 205 may be fitted into the first radial inner surface 120 during the construction of the antenna. For example, the first radiator 205 may be machined from a conductive material and bonded to the first radial inner surface 120 with epoxy resin. As another example, the first radiator 205 may be formed by electrolytic emission of a conductor onto a dielectric base, inserted into a cavity on the radially inward side of the first radial inner surface 120, fitted into the first radial inner surface 120, and secured by a dielectric mass and a metal top hat or dielectric top hat. The first radiator 205 may be formed directly on the first radial inner surface 120. For example, the first radiator 205 may be formed by spraying a conductive ink or dispersion onto the first radial inner surface 120.

[0085] In certain embodiments, the first radiator 205 may be electrically coupled to a transmission line. For example, the first radiator 205 may be soldered, welded, or joined to a pin extending from the center conductor of the transmission line. Alternatively, a pin extending from the center conductor of a coaxial connector may be press-fitted into the first radiator 205. Coupled the first radiator 205 to the transmission line excites an RF current in the first radiator 205 over a broadband.

[0086] In certain embodiments, the first radiator 205 can be fitted to or electrically coupled to a top hat. For example, the first radiator 205 can be fixed within the dielectric mass 110 by a dielectric top hat fastened to the dielectric mass 110. In another example, the first radiator 205 is conductively bonded with epoxy resin to a conductive top hat that prevents current from flowing radially inside the first radiator 205 in its maximum longitudinal dimension.

[0087] The internal ground 210 is located radially outside the dielectric block 110, as shown in Figures 2A and 2B, and presents a conductive surface at the inner ground plane 140. The internal ground 210 may also present a conductive surface at one or more edges 150B between the inner ground plane 140 and the non-conductive aperture surface 130. In the antenna 200, RF energy propagates between the first conductive surface presented by the first radiator 205 and the second conductive surface presented by the internal ground 210. The RF energy propagates between these two conductive surfaces from the transmission line through the dielectric block 110 to the non-conductive aperture surface 130 (transmission), and from the non-conductive aperture surface 130 through the dielectric block 110 to the transmission line (reception). The internal ground 210 may extend longitudinally and radially from the base 160 to one or more edges 150B or the non-conductive aperture surface 130. The internal ground 210 may be azimuthally uniform or radially symmetric. In certain embodiments, the internal ground 210 may extend to the maximum longitudinal radius of the dielectric mass 110. In certain embodiments, the internal ground 210 may include a convex surface, a concave surface, or both convex and concave surfaces.

[0088] The internal ground 210 may be formed by machining, additive manufacturing, sintering, stamping, spraying, rolling, or deposition processes, or from one or more similar processes. For example, the internal ground 210 may be machined or additive manufactured from a conductive material (e.g., copper or aluminum) such that the internal ground 210 fills the space between the inner ground surface 140 and the outer ground. As another example, the internal ground 210 may be formed without a conductive mass by depositing a second conductive surface on the inner ground surface 140. As yet another example, the internal ground 210 may be formed without a conductive mass by stamping a conductive sheet and bonding it to the inner ground surface 140. As yet another example, the internal ground 210 may be formed integrally with the outer ground (e.g., by machining or stamping as part of a larger ground structure) and fitted into the inner ground surface 140. In certain embodiments, forming the internal ground 210 without a conductive mass may have the advantage of reducing the size and weight of the antenna 200. In certain embodiments, the internal ground 210 may be formed of a conductive mass to facilitate mating to the dielectric mass 110, to facilitate mating to an external ground or external platform, or to enhance the structural integrity of the internal ground 210. For example, the internal ground 210 may be formed to a thickness sufficient to facilitate conductive bonding of the external ground to the internal ground 210 with epoxy resin, mechanical fastening, or otherwise bonding. In certain embodiments, the external ground may be coupled to the internal ground 210 via one or more edges 150B. Coupled with the internal ground 210 may have the advantages of isolating the antenna 200 from cabling and RF circuits, increasing the gain of the antenna 200, and facilitating installation of the antenna 200 on various platforms.

[0089] In certain embodiments, the internal ground 210 may be formed by arranging one or more conductive surfaces on the dielectric substrate. For example, the internal ground 210 may be formed without a conductive mass by electroplating copper onto the dielectric substrate. As another example, the internal ground 210 may be formed by stamping one or more conductive sheets and fitting the stamped sheets onto the dielectric substrate. Forming the internal ground 210 by arranging conductive surfaces on the dielectric substrate may have one or more advantages, including reducing the size and weight of the antenna, enhancing the structural integrity of the internal ground 210, reducing RF loss by presenting a smooth conductive surface to the associated RF energy (our RF energy) passing through the dielectric mass, and facilitating a non-selective process for presenting conductive surfaces on the internal ground surface 140. For example, forming the internal ground 210 on the dielectric substrate may allow electroplating of the entire surface on the dielectric substrate without masking. The dielectric base in the internal ground 210 may consist of the dielectric mass 110, any dielectric material discussed with respect to the first radiator 205, or any dielectric material suitable for mating, depositing, and bonding a conductive surface onto the dielectric base.

[0090] In certain embodiments, the internal ground 210 can be fitted to the internal ground surface 140 during the construction of the antenna. For example, the internal ground 210 can be machined from a conductive material and bonded to the internal ground surface 140 with epoxy resin. Alternatively, the internal ground 210 can be formed by electrolytic deposition of a conductor onto a dielectric substrate, bonded to the internal ground surface 140 with epoxy resin, and secured by the dielectric mass and the external ground. The internal ground 210 can also be formed directly on the internal ground surface 140. For example, the internal ground 210 can be formed by spraying a conductive ink or dispersion onto the internal ground surface 140.

[0091] In certain embodiments, the internal ground 210 may be electrically coupled to the transmission line. For example, the internal ground 210 may be soldered, welded, or joined to the outer conductor or ground conductor of the transmission line. As another example, the outer conductor of a coaxial connector (e.g., a flanged connector) may be fastened into the internal ground 210. Coupled the internal ground 210 to the transmission line excites RF currents in the internal ground 210 over a wide bandwidth.

[0092] In certain embodiments, the internal ground 210 may increase the height of the antenna 200. As shown in Figure 2A, for example, the internal ground 210 extends beyond the minimum longitudinal portion of the dielectric block 110. Extending the internal ground 210 may have one or more advantages, including controlling the gain and direction at a particular frequency, and facilitating the insertion of fasteners into the internal ground 210. In certain embodiments, the internal ground 210 may not extend beyond the minimum longitudinal portion so that the height of the antenna 200 is the same as the height of the dielectric block 110 (for example, the internal ground 210 does not extend longitudinally beyond the base 160).

[0093] In certain embodiments, the internal ground 210 can be mated to or electrically coupled to an external ground. For example, the internal ground 210 can be fixed by fastening to the external ground. As another example, the internal ground 210 can be electrically bonded to the external ground with epoxy resin. In certain embodiments, the internal ground 210 can be formed integrally as part of a larger ground structure. For example, the internal ground 210 and the external ground can be formed together by stamping a conductive sheet, or the internal ground 210 and the external ground can be machined from a single conductive mass (e.g., a block of aluminum).

[0094] The external ground 220 may be any ground structure for mating to or electrically coupling to the antenna 200. In certain embodiments, the external ground 220 may be mated to or electrically coupled to the internal ground 210. In certain embodiments, the external ground 220 may be part of a larger platform. For example, the external ground 220 may be part of the aluminum casing of an aircraft. In the radiation patterns disclosed herein, any external ground may coincide with the azimuth plane (XY, θ=90°).

[0095] As shown in Figure 2A, the external ground 220 is located at the minimum longitudinal portion of the internal ground 210. In certain embodiments, the external ground 220 may be located at the maximum longitudinal portion of the internal ground. For example, the external ground 220 may be electrically bonded with epoxy resin to the maximum longitudinal portion of the internal ground 210 (for example, at one or more edges 150B between the internal ground 210 and the non-conductive opening surface 130). In embodiments where the internal ground 210 is formed without a conductive mass, the external ground 220 may be electrically bonded with epoxy resin to the second conductive surface (and thus the internal ground 210) at one or more edges 150B adjacent to the internal ground 210, or at a base 160 adjacent to the internal ground 210. In embodiments where there are no one or more edges 150B adjacent to the internal ground surface 140, the external ground 220 may be fitted to the internal ground 210. In certain embodiments, the antenna 200 may not include an inner ground 210 such that the outer ground 220 directly mates with the inner ground surface 140.

[0096] In certain embodiments, the external ground 220 may be electrically coupled to the transmission line. In certain embodiments, the external ground 220 may be electrically coupled to the transmission line indirectly via the internal ground 210. In certain embodiments, both the internal ground 210 and the external ground 220 may be directly coupled to the outer conductor or ground conductor of the transmission line.

[0097] The transmission line 230 can be any suitable transmission line for transmitting and receiving RF energy. The inner conductor or signal conductor of the transmission line 230 may be electrically coupled to the first radiator 205. The outer conductor or ground conductor of the transmission line 230 may be electrically coupled to the internal ground 210, the external ground 220, or both. The transmission line 230 may include a transmission line dielectric (such as the transmission line dielectric 170 in Figure 1) that separates the inner conductor or signal conductor from the outer conductor or ground conductor of the transmission line. In certain embodiments, the transmission line dielectric may be fitted to the base of a dielectric mass. In certain embodiments, the transmission line 230 may be azimuthally uniform or radially symmetric. In certain embodiments, the transmission line 230 may couple the antenna 200 to the transceiver.

[0098] In certain embodiments, the dielectric of the transmission line 230 may extend longitudinally beyond the longitudinal minimum of the dielectric mass 110. For example, referring to Figure 1, the transmission line dielectric 170 may extend longitudinally beyond the base 160, or, in embodiments without a base 160, beyond the longitudinal minimum of the inner ground plane 140. Extending the transmission line dielectric longitudinally may have the advantages of protecting the transmission line central conductor (including the pin coupled to the first radiator 205), fixing the dielectric mass 110, and fixing the longitudinal position of the transmission line 230 relative to the dielectric mass 110. Embodiments in which the transmission line dielectric is extended longitudinally have little effect on RF performance and can obtain the radio performance disclosed herein with respect to the antenna 200.

[0099] Figure 2B shows a perspective view of the antenna 200. The diagram in Figure 2B corresponds to the cross-sectional view of Figure 2A rotated with respect to the radial symmetry axis (the Z-axis at the center of the antenna 200). As shown in Figure 2B, the antenna 200 comprises a first radiator 205, a dielectric mass 110, and an internal ground 210, and the antenna 200 is coupled to an external ground 220. The transmission line 230 is not shown in Figure 2B. As shown in Figure 2B, the first radiator 205 is positioned on the first radial inner surface 120 of the dielectric mass 110 to form an integrated dielectric unit. The first radiator 205 can also be formed according to any method described above with respect to Figure 2A and fitted into the dielectric mass 110. In Figure 2B, the dielectric mass 110 is fitted into the internal ground 210. For example, the dielectric mass 110 can be fastened to the internal ground 210 by mechanical fasteners such as nylon screws, or it can be bonded to the internal ground 210 by epoxy resin. The internal ground 210 mates to the external ground 220 in Figure 2B. As described in Figure 2A, the external ground 220 may be part of a flat ground plane or an external platform. In certain embodiments, the internal ground 210 may mate directly to an external structure, such as a mast, tower, fabric (in the case of a body-worn application), or a similar mechanism for fixing the position of the antenna 200, without the external ground 220.

[0100] Antenna 200 can be fabricated according to several methods, including methods for fabricating the subcomponents of antenna 200 (first radiator 205, dielectric block 110, internal ground 210) as described above.

[0101] Antenna 200 can be formed from a dielectric block 110. In certain embodiments, the first radiator 205, the inner ground 210, or both can be disposed on the surface of the dielectric block 110 to form an integrated dielectric unit. In certain embodiments, the dielectric block and one or more conductive surfaces together form a dielectric unit without a conductive block. As described above with respect to the first radiator 205 and the inner ground 210, a first conductive surface can be disposed on the first radially inner surface 120 to form the first radiator 205 (and can include any adjacent edge 150A), and a second conductive surface can be disposed on the inner ground surface 210 (and can include any adjacent edge 150B). For example, FIG. 2 shows a first radiator 205 formed by disposing a first conductor on the first radially inner surface 120 and an inner ground 210 formed by machining a conductive block and fitting the inner ground 210 to the inner ground surface 140 and the edge 150B. To form the inner ground 210 without a conductive block, the inner ground 210 can instead be formed by disposing a second conductive surface on the inner ground surface 140.

[0102] In certain embodiments, due to the thinness of the conductive surface disposed on the dielectric block, the dielectric unit has substantially the same dimensions and weight as the dielectric block. Disposing a conductive surface on the dielectric block can significantly reduce the size, weight, and manufacturing complexity of the antenna. The conductive surface is thin and lightweight and can be integrated with the dielectric block to form a single dielectric unit configured for wireless transmission and reception.

[0103] In certain embodiments, forming the dielectric block (and the dielectric unit) as a single integrated unit realizes a significant reduction in size and weight. In FIGS. 2A and 2B, the height of the antenna 200 is 0.19λ L weak, the radius is 0.08λ L weak, and the maximum height of the inner ground 210 is 0.03λL. In certain embodiments, the weight of the dielectric unit is 2.4 - 3.6 kg / m 3This is obtained by multiplying by the cube of the minimum operating wavelength (in meters). With POSITA, it will be understood that the size and weight of the antenna are generally proportional to the cube of the wavelength. With POSITA, it will also be understood that the weight of the dielectric unit can be calculated by determining the dielectric mass based on the minimum operating wavelength and the maximum antenna dimensions of antenna 200 and multiplying by the specific gravity value disclosed herein. For other embodiments disclosed herein, similar calculations can be performed based on the dimensions described and illustrated herein to determine the corresponding volume and weight.

[0104] In certain embodiments, the antenna 200 may be formed to include one or more conductive blocks. For example, as shown in Figure 2B, the antenna 200 may include an internal ground 210 machined from a block of aluminum. Including one or more conductive blocks in the antenna 200 may provide certain advantages, such as providing a mating structure for fasteners or facilitating electrical coupling with an external structure (e.g., an external ground 220 or a transmission line 230).

[0105] In certain embodiments, the antenna 200 may be formed to have conductive surfaces on one or more dielectric bases. For example, the first radiator 205 and the internal ground 210 may be formed by arranging a first conductive surface and a second conductive surface on a dielectric base, respectively. Providing the antenna 200 with one or more dielectric bases may offer certain advantages, such as reducing the weight of the antenna, facilitating a non-selective process for arranging the conductive surfaces of the antenna 200, and presenting a smooth conductive surface to RF energy to reduce RF loss.

[0106] In certain embodiments, the dielectric mass 110, the first radiator 205, and the internal ground 210 may be assembled into an antenna 200. In certain embodiments, the first radiator 205 or the internal ground 210 may be placed on the surface of the dielectric mass to form an integrated dielectric unit. In certain embodiments, the first radiator 205, the internal ground 210, or both may be fitted into the dielectric mass 110. For example, the first radiator 205 or the internal ground 210 may be fitted into the dielectric mass using fasteners, adhesive, bonding, press-fit, interlocking, or similar methods. In certain embodiments, the first radiator 205 may be fixed to the dielectric mass 110 via a top hat, although this is not shown in Figures 2A and 2B.

[0107] Antenna 200 can be configured for transmitting and receiving radio signals in various frequency bands. In particular, antenna 200 can be configured for instantaneously transmitting and receiving wideband radio signals with high fidelity. For example, antenna 200 can be configured to instantaneously transmit and receive radio signals with fidelity of 90% or more over a bandwidth of up to 6:1 (instantaneous bandwidth). Antenna 200 can also be configured to instantaneously transmit and receive radio signals with fidelity of 75% or more over a bandwidth of up to 8:1 (instantaneous bandwidth). As shown in Figure 2, antenna 200 can be further configured to transmit and receive omnidirectional radiation patterns over a wide frequency band with a bandwidth of up to 6:1 (pattern bandwidth). Antenna 200 can also be configured to transmit and receive conical beams over a wide frequency band with a bandwidth of up to 6:1 (pattern bandwidth). In certain embodiments, the pattern bandwidth described in this paragraph corresponds to the instantaneous bandwidth described in this paragraph. Antenna 200 can be configured to maintain a return loss of 10 dB or more over the pattern bandwidth and instantaneous bandwidth described in this paragraph. In certain embodiments, the antenna 200 may be configured to maintain a return loss of 6 dB or more over the pattern bandwidth and instantaneous bandwidth described in this paragraph.

[0108] Many of the structures, components, configurations, techniques, parameters, principles, and methods disclosed with reference to Figures 1 and 2 may be used in other embodiments described herein. For example, the embodiments disclosed with reference to Figure 1 and Figures 2A and 2B may also be used in antennas 500 (Figures 5A and 5B) and 800 (Figure 8A), which share a common topology with antenna 200 but have different dimensions to achieve different radio performance metrics. The embodiments disclosed with reference to Figure 1 and Figures 2A and 2B may also be used in antennas 1000 (Figures 10A and 10B), 1300 (Figures 13A to 13C), 1600 (Figures 16A to 16C), 1900 (Figures 19A to 19C), 2400 (Figure 24), and 2700 (Figures 27A and 27B), provided they are compatible with their respective antenna topologies.

[0109] Figures 3 and 4 summarize the overall wireless performance of antenna 200, including the radiation pattern over a 6:1 bandwidth (1 to 6 fL) and the return loss and time-domain performance over a 12:1 bandwidth (1 to 12 fL).

[0110] Figure 3 shows the overall radiation pattern of antenna 200 at various frequencies in the main cross-section. 3 Figures 3A and 3B show the radiation patterns of antenna 200 maintaining two modes over a 6:1 pattern bandwidth, one of which radiates a beam with substantially uniform gain in the azimuth angle including the radiation horizon ("horizontal beam"). 4On the other hand, the antenna radiates a conical beam at an elevation angle (θ) of approximately 30° from the radial symmetry axis. Although not shown in Figures 3A and 3B, antenna 200 maintains both a horizontal and a conical beam over a 12:1 pattern bandwidth (1 to 12 fL). Figures 3C and 3D show the radiation pattern in the azimuth plane (XY, θ=90°) from 1.5 to 6 fL. The azimuth plane gain at 1 fL is in the range of -0.11 dBi to 0 dBi. Although Figures 3C and 3D only show the pattern from 1.5 to 6 fL, the azimuth plane pattern of antenna 200 is substantially uniform over the 12:1 pattern bandwidth (1 to 12 fL), with a maximum variation of ±1.2 dB at 5 fL. Figures 3E and 3F show the radiation pattern from 1.5 to 6 fL at an elevation angle θ=30° from the radial symmetry axis. The gain of the θ=30° cross-section at 1 fL is uniform at -3 dBi. Figures 3E and 3F show only the patterns from 1.5 to 6 fL, but antenna 200 maintains a conical beam up to a maximum of 12 fL. 3 The performance shown in Figures 3 and 4 is the same as the radius (≤λ) of the dielectric block. L This relates to antenna 200 equipped with a ground plane having a 12-degree angle ( / 12). 4 Those skilled in the art will understand that an antenna radiating a beam containing a horizontal line may mean that the horizontal line is contained within the 3 dB elevation beamwidth of the beam, or that the horizontal line lies within the null (minimum) that defines the beamwidth at the elevation angle of the beam, as indicated by the radiation pattern described (for example, the pattern shown in Figures 3A and 3B).

[0111] Figures 4A and 4B show exemplary time-domain responses of antenna 200. Figure 4A shows the time-domain response of antenna 200 for radio signals transmitted and received in a horizontal beam (θ=90°) covering 1–4 fL. in V indicates the input signal at the transmitting antenna 200, out This indicates the output signal at the receiving antenna 200. As shown in Figure 4A, the input signal V in and output signal V outBy determining the cross-correlation with the total signal energy and normalizing it, a fidelity of 75% can be obtained.

[0112] As shown in Figures 4A and 4B and similar time-domain responses disclosed herein, the fidelity coefficient is for signals transmitted and received in a two-port model (from transmitting antenna to receiving antenna) (corresponding to the transmitted signal S, Vin in Figures 4A and 4B). t ) Input signal and (Received signal S corresponding to Vout in Figures 4A and 4B) r ) This is calculated as the maximum normalized cross-correlation between the output signal and the signal:

number

[0113] Table 1 summarizes the fidelity of radio signals across different IBWs in the horizontal beam of Antenna 200. Although not shown in Table 1, the fidelity of Antenna 200 in the 1.5 fL bandwidth (e.g., 1.5–3 fL, 3–4.5 fL, 4.5–6 fL) exceeds 85%. Antenna 200 can instantaneously transmit or receive radio signals across IBWs up to 8:1 (1.5–12 fL) with fidelity exceeding 75%. Antenna 200 can also instantaneously transmit or receive radio signals across IBWs up to 10.5 fL (1.5–12 fL) with fidelity exceeding 75%. As shown in Table 1, Antenna 200 can also instantaneously transmit or receive radio signals across bandwidths up to 12:1 by instantaneously transmitting or receiving signals in one or more instantaneous frequency bands, each having at least the lowest operating frequency IBW.

[0114] [Table 1]

[0115] Figure 4B shows the time-domain response of antenna 200 to radio signals transmitted and received with a conical beam (θ=30°) covering 1.5–7.5 fL. inV indicates the input signal at the transmitting antenna 200, out This indicates the output signal at the receiving antenna 200. As shown in Figure 4B, the input signal V in and output signal V out By determining the cross-correlation and normalizing it with respect to the total signal energy, a fidelity of 91% is obtained. Table 2 summarizes the signal fidelity across various IBWs for the conical beam of antenna 200. Although not shown in Table 2, the fidelity of antenna 200 in a 1 fL bandwidth (e.g., 6-7 fL, 7-8 fL, 8-9 fL, 9-10 fL, 10-11 fL, and 11-12 fL) exceeds 90%. Antenna 200 can instantaneously transmit or receive radio signals over IBWs up to 8:1 (1.5-12 fL) with a fidelity of over 75%. Antenna 200 can also instantaneously transmit or receive radio signals over IBWs up to 10.5 fL (1.5-12 fL) with a fidelity of over 75%. Antenna 200 can also instantaneously transmit or receive radio signals over a bandwidth of up to 12:1 by instantaneously transmitting or receiving signals in one or more instantaneous frequency bands, each having at least the lowest operating frequency IBW.

[0116] [Table 2]

[0117] The fidelity in this disclosure is calculated using Gaussian excitation (Gaussian envelope multiplied by a sinusoidal carrier with center frequency fc) with a center frequency at the center of the modeled bandwidth and a 20 dB cutoff frequency at the edge of the modeled bandwidth. Similar fidelity can be obtained for other signal types. For example, the fidelity in Tables 1 and 2 can also be obtained for direct sequence spread spectrum signals. As another example, the fidelity in Tables 1 and 2 can also be obtained for signals with a flat power spectral density across the signal bandwidth, such as a White Gaussian signal. To avoid confusion, the term “Gaussian excitation” refers to a Gaussian amplitude envelope applied to a sinusoidal carrier. On the other hand, the term “Gaussian signal” refers to a signal with the stochastic characteristics of Gaussian noise.

[0118] Antenna 200 has substantially the same pattern and fidelity characteristics as those described in Figures 3 and 4, even without an outer ground plane. λ L A ground with a radius of 12 lowers the minimum operating frequency at which return loss is achieved or exceeded, but has little effect on fidelity, pattern, or IBW. Therefore, placing antenna 200 or a variation thereof on a larger external ground plane can extend the minimum operating frequency while maintaining substantially the same pattern and fidelity performance as described herein.

[0119] For example, as shown in Figures 4C to 4D, the return loss of antenna 200 exceeds 10 dB over an efficiency bandwidth of 12:1.45, regardless of the size of the ground plane on which antenna 200 is placed. As used herein, the term “ground plane” refers to the external ground 220 (or its equivalent in various embodiments) unless expressly otherwise stated. Figure 4C shows (λ L From the radius of the ground plane of / 12 λ L This plots the return loss of Antenna 200 placed on ground planes of various sizes (within the range of a ground plane radius of λ). LFor ground planes with a radius of λ or greater, the return loss is substantially 10 dB or more over a bandwidth of at least 10:1 (1.2–12 fL). L For ground planes of λ or larger, the return loss is substantially 6 dB or more over at least a 12:1 bandwidth (1–12 fL). As shown in Figure 4C, the size of the ground plane has virtually no effect on the return loss performance beyond 2 fL (i.e., the return loss beyond 2 fL remains 10 dB or more for all ground sizes). L As shown in Figure 4D, which exhibits a return loss of 2 to 12 fL for a ground plane size of / 12, antenna 200 maintains a return loss of over 10 dB up to a maximum of 12 fL.

[0120] Therefore, for antenna 200, the placement is unaffected by the return loss threshold of 10 dB above 1.5 fL, and for the return loss threshold of 6 dB above 1 fL. The size of the ground plane does not affect the return loss above the 10 dB threshold at frequencies above 2 fL, and at frequencies above 1.5 fL, the return loss exceeds 10 dB regardless of the size of the ground plane.

[0121] Antenna 200 may be configured to obtain desirable radio performance, including a small antenna size, a wide efficiency bandwidth (bandwidth where the return loss substantially achieves or exceeds a metric, such as 6 dB or 10 dB), a wide instantaneous bandwidth (bandwidth where the IBW, fidelity, etc., achieves or exceeds a metric, such as 90%), and a wide pattern bandwidth (bandwidth where the radiation pattern achieves or exceeds a metric, such as maintaining a specific gain threshold, conical beam, or horizontal beam). For example, the topology of antenna 200 determines the position, profile, dimensions, and interaction of the first radiator 205, internal ground 210, and non-conductive aperture surface 130 to facilitate maximizing the efficiency bandwidth, IBW, pattern bandwidth, and the overlap between the efficiency bandwidth, IBW, and pattern bandwidth. Other antenna embodiments disclosed herein similarly determine the position, profile, dimensions, and interaction of the antenna features to facilitate obtaining wide IBW, efficiency, and pattern performance.

[0122] Figure 5 shows the overall geometric shape and features of antenna 500 in two cross-sectional views. Figure 5A does not include conductive surfaces or conductive blocks. Antenna 500 has the same topology as antenna 200, but has different physical dimensions, particularly smaller radial dimensions to enable broadband beam scanning in the antenna array.

[0123] The antenna 500 may be formed from a dielectric block 510. As shown in Figure 5A, the dielectric block 510 may have multiple surfaces, including a first radial inner surface 520, a non-conductive aperture surface 530, an inner ground surface 540, edges 550A, 550B, and a base 560. The dielectric block 510 may be fitted into a transmission line dielectric 570. To facilitate reference to various physical features and radio performance characteristics (particularly radiation patterns), Figure 5A also shows an azimuthal plane 580, a radiation symmetry axis 590 located at the radiation center of the antenna 500, and an XYZ coordinate system.

[0124] As shown in Figure 5A, the dielectric mass 510 is azimuthally uniform (without variation according to φ), as can be seen when a cross-section is taken in an arbitrary elevation plane (θ-r plane) to obtain the diagram in Figure 5A. Rotating the cross-sectional views in Figures 5A and 5B about the radial symmetry axis 590 yields a three-dimensional dielectric mass 510 in which each face in the three-dimensional view has multiple surfaces corresponding to the curves in the cross-sectional views in Figures 5A and 5B. The dielectric mass 510 can be radially symmetric or azimuthally uniform with respect to the radial symmetry axis 590. The dielectric mass 510 terminates radially inward at the first radial inner surface 520. The dielectric mass 510 terminates radially outward at the non-conductive opening surface 530. The dielectric mass 510 terminates at the longitudinal maximum of one or more edges 550A. Figure 5A shows one edge 550A at the longitudinal maximum of the dielectric mass 510. The dielectric mass 510 terminates at its shortest longitudinal portion in the base 560. The dielectric mass 510 also has an inner ground surface 540 extending radially outward from the base 560 to one or more edges 550B or nonconductive opening surfaces 530.

[0125] In certain embodiments, the dielectric mass 510 has a maximum radius determined by the maximum radial dimension of the non-conductive opening surface 530. In certain embodiments, the dielectric mass 510 has a maximum height determined as the longitudinal distance from the base 560 to the maximum longitudinal portion of the dielectric mass 510. As shown in Figure 5A, the maximum radius of the dielectric mass 510 is λ L The height of the dielectric block 510 is λ, and does not exceed / 20. L Do not exceed / 5.

[0126] The first radial inner surface 520 may have the same or similar configuration, features, interface, parameters, or functions as the first radial inner surface 120 on the dielectric mass. The non-conductive aperture surface 530 may have the same or similar configuration, features, interface, parameters, or functions as the non-conductive aperture surface 130 on the dielectric mass. The inner ground surface 540 may have the same or similar configuration, features, interface, parameters, or functions as the inner ground surface 140 on the dielectric mass. One or more edges 550A, 550B may have the same or similar configuration, features, interface, parameters, or functions as the edges 150A, 150B on the dielectric mass. The transmission line dielectric 570 may have the same or similar configuration, features, interface, parameters, or functions as the transmission line dielectric 170. Note that the size and dimensions of the first radial inner surface 520, the non-conductive opening surface 530, the inner ground surface 540, one or more edges 550A, 550B, and the base 560 correspond to the antenna 500 shown in Figure 5, not the antenna 200.

[0127] The azimuthal plane 580 defines the radial horizon (θ=90°). In certain embodiments, the azimuthal plane 580 may also define an azimuthal plane (θ=90°, XY) corresponding to the external ground plane. The radial symmetry axis 590 defines the Z axis, and with respect to the Z axis, the dielectric mass 510 (and antenna 500) are azimuthally uniform or radially symmetric.

[0128] The dielectric mass 510 may be formed from any fabrication process, material, or composition of material described herein with respect to other dielectric masses disclosed herein, which conform to the topology of the dielectric mass 510 shown in Figure 5.

[0129] Figure 5B shows a cross-sectional view of antenna 500, which includes a conductive surface and a conductive mass. As shown in Figure 5, antenna 500 is azimuthally uniform. A perspective view of antenna 500 corresponding to the cross-sectional view in Figure 5B can be generated by rotating the cross-sectional view in Figure 5B with respect to the radial symmetry axis 590.

[0130] The first radiator 505 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as the first radiator 205 in the antenna, except that the size and dimensions of the first radiator 505 correspond to antenna 500 instead of antenna 200. The first radiator 505 may be formed in the same or similar manner, operation, steps, parameters, and principles as the first radiator 205, and from the same or similar materials as the first radiator 205.

[0131] The internal ground 515 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as the internal ground 210 in the antenna, except that the size and dimensions of the internal ground 515 correspond to antenna 500 rather than antenna 200. As shown in Figure 5B, the internal ground 515 does not extend beyond the minimum longitudinal portion of the dielectric block 510, so that the height of antenna 500 is the same as the height of the dielectric block 510. The internal ground 515 may be formed in the same or similar manner, operation, steps, parameters, and principles as the internal ground 210, and from the same or similar material as the internal ground 210.

[0132] The external ground 525 in the antenna may have the same or similar structure, components, elements, configuration, features, interface, parameters, or functions as the external ground 220. The transmission line 535 may have the same or similar structure, components, elements, configuration, features, interface, parameters, or functions as the transmission line 230.

[0133] Figures 6 and 7 show the overall radiation pattern, return loss, and time-domain performance of antenna 500 over a 12:1 bandwidth (1 to 12 fL). 5 This summarizes the performance of the device. 5 The performance shown in Figures 6 and 7 is the same as the radius (≤λ) of the dielectric mass. L This relates to antenna 500 equipped with a ground plane having a 20-degree angle ( / 20).

[0134] Figures 6A to 6C show the return loss and exemplary time-domain response of antenna 500. The return loss of antenna 500 in Figure 6A is substantially 10 dB or more over an efficiency bandwidth of 1.33 to 6 fL and 6 dB or more over an efficiency bandwidth of 1.25 to 6 fL. Those skilled in the art will understand that small adjustments to the return loss can be made by changing the geometric shape of antenna 500 (e.g., by adjusting the profiles of the non-conductive aperture surface 530, the first radial inner surface 520, or the edges 550A, 550B) without substantially affecting the radiation pattern or time-domain performance of antenna 500.

[0135] Figure 6B shows an exemplary time-domain response of Antenna 500 when transmitting or receiving a radio signal in a horizontal beam (θ=90°) with an IBW of 2–4 fL. Table 3 summarizes the fidelity of Antenna 500 in the horizontal beam with respect to radio signals across different IBWs. Although not shown in Table 3, the fidelity of Antenna 500 in the 1.5 fL bandwidth (e.g., 1.5–3 fL, 3–4.5 fL, 4.5–6 fL) exceeds 85%, and the fidelity of Antenna 500 in the 2.5 fL bandwidth (e.g., 1–3.5 fL, 3.5–6 fL) exceeds 75%. The antenna can instantaneously transmit or receive radio signals in the horizontal beam with an IBW of at least up to 3.5:1 (1–3.5 fL). The antenna can also instantaneously transmit or receive radio signals in the horizontal beam with an IBW of up to 2.5 fL across various bandwidths. Antenna 500 can also instantaneously transmit or receive radio signals over a bandwidth of up to 6:1 by instantaneously transmitting or receiving signals in one or more instantaneous frequency bands, each having at least the lowest operating frequency IBW.

[0136] [Table 3]

[0137] Figure 6C shows an exemplary time-domain response of Antenna 500 when transmitting or receiving radio signals at IBWs of 1–6 fL in a conical beam (θ=30°). Table 4 summarizes the fidelity of Antenna 500 for radio signals across different IBWs in a conical beam. Although not shown in Table 4, the fidelity of Antenna 500 in the 1.5 fL bandwidth (e.g., 1.5–3 fL, 3–4.5 fL, 4.5–6 fL) exceeds 95%. Antenna 500 can instantaneously transmit or receive radio signals over IBWs of up to 8:1 (1.5–12 fL) in a conical beam. Antenna 500 can also instantaneously transmit or receive radio signals over IBWs of up to 10.5 fL (1.5–12 fL) in a conical beam. Antenna 500 can also instantaneously transmit or receive radio signals over a bandwidth of up to 12:1 by instantaneously transmitting or receiving signals in one or more instantaneous frequency bands, each having at least the lowest operating frequency IBW.

[0138] [Table 4]

[0139] Figure 7 shows the radiation pattern of antenna 500 in the main cross-section at various frequencies. Figures 7A and 7B show the radiation pattern of antenna 500 maintaining two modes: one radiating a beam with substantially uniform gain at azimuth angles including the radiation horizon ("horizontal beam"), and the other radiating a conical beam at an elevation angle (θ) of 30° from the radiation axis of symmetry. Antenna 500 maintains both horizontal and conical beams over a 6:1 pattern bandwidth (1–6 fL). Figures 7C and 7D show the radiation pattern in the azimuth plane (XY, θ=90°) from 2–6 fL. The gain in the azimuth plane at 1 fL is substantially uniform in the range of -6 to -6.2 dBi, and the gain in the azimuth plane at 1.5 fL is substantially uniform in the range of 1.0 to 1.2 dBi. Figures 7C and 7D show only the patterns from 2 to 6 fL, but the azimuthal plane pattern of antenna 500 is substantially uniform over a 6:1 pattern bandwidth (1 to 6 fL), with a maximum variation of ±1.8 dB at 5.5 fL. Figures 7E and 7F show the radiation patterns from 2 to 6 fL at an elevation angle θ = 30° from the radiation symmetry axis. The gain at the θ = 30° cross-section at 1 fL is uniform at -8.8 dBi, and at 1.5 fL it is substantially uniform at -2.1 to -2.2 dBi. As can be seen from Figures 7A and 7B and Figures 7E and 7F, antenna 500 maintains a conical beam from 1 to 6 fL.

[0140] Antenna 500 is λ L Considering the minimum ground spread from a ground radius of / 20, even without an outer ground plane, the pattern and fidelity characteristics are substantially the same as those described in Figures 6-7 and Tables 3 and 4. L A ground with a radius of 20 lowers the minimum operating frequency at which return losses of 10 dB and 6 dB are achieved, but has little effect on fidelity, pattern, or IBW. Therefore, placing the antenna 500 or a variation thereof on a larger external ground plane can extend the minimum operating frequency while maintaining substantially the same pattern and fidelity performance as described herein.

[0141] In certain embodiments, the antenna 500 may be an antenna element of an antenna array having beam scanning capability over a 5:1 bandwidth. L With a maximum radius of 20, a half-wavelength spacing between antenna elements is permitted up to 5 fL. In certain embodiments, a plurality of dielectric blocks 510 may be formed as a single, integrated dielectric array unit having an antenna array formed by arranging conductive surfaces on the dielectric array unit and mating transmission lines to the dielectric array unit. The dielectric array unit may be formed in the same or similar manner, operation, steps, parameters, and principles as any dielectric unit described herein. Individual dielectric units integrated into the dielectric array unit may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions in the antenna array as any dielectric unit described herein.

[0142] In certain embodiments, the first and second antennas may be separated by a distance not exceeding half a wavelength at the highest operating frequency. For example, two antennas 500 operating over a 5:1 bandwidth may be separated by half a wavelength at the highest operating frequency of that bandwidth. In certain embodiments, the highest operating frequency is determined by the radial dimensions of the first and second antennas.

[0143] In certain embodiments, the first and second antennas may be separated by a distance of more than half a wavelength at the highest operating frequency. In certain embodiments, the highest operating frequency may be the frequency at which the array pattern of the antenna array scanned across the spatial sector exhibits a secondary lobe (such as a grating lobe) with a gain at least 10 dB lower than the primary lobe.

[0144] In certain embodiments, the first and second antennas are configured to transmit or receive radio signals in the spatial sector and not transmit or receive radio signals outside the spatial sector, based on a time delay between the signal received by the first antenna and the signal received by the second antenna. In certain embodiments, the first and second antennas may be configured to transmit or receive radio signals in a quadrant with an azimuth angle of 90 degrees. Alternatively or additionally, the first and second antennas may be configured to transmit or receive radio signals in a sector with an elevation angle of 30 degrees.

[0145] In certain embodiments, the signals transmitted or received by the first and second antennas may have an IBW of up to 4:1. Alternatively or additionally, the signals transmitted or received by the first and second antennas may have an IBW of up to 5:1, 6:1, or 8:1. The first and second antennas, and their arrangement and orientation within the antenna space, may be configured to instantaneously transmit or receive radio signals over an IBW of up to 4:1, 5:1, 6:1, or 8:1.

[0146] In certain embodiments, the first and second antennas are configured to radiate a pattern including a radiation horizon (i.e., an azimuth plane) over a pattern bandwidth of up to 5:1 or 6:1. In certain embodiments, the first and second antennas are configured to radiate a pattern including a beam that is substantially uniform in azimuth, either separately or together.

[0147] In certain embodiments, the first and second antennas may be configured to transmit or receive radio signals in the spatial sector and not transmit or receive radio signals outside the spatial sector, based on a phase delay between the signal received by the first antenna and the signal received by the second antenna. In certain embodiments, the phase delay may be a constant phase shift across the relevant bandwidth. In certain embodiments, the first and second antennas may be configured to transmit or receive radio signals in the quadrant with an azimuth angle of 90 degrees. Alternatively or additionally, the first and second antennas may be configured to transmit or receive radio signals in the sector with an elevation angle of 30 degrees.

[0148] In certain embodiments, the first and second antennas may be configured to transmit or receive signals over an efficiency bandwidth of up to 6:1. Alternatively or additionally, the first and second antennas may be configured to transmit or receive signals over an efficiency bandwidth of 12:1. In certain embodiments, the first and second antennas may be configured to transmit or receive signals over an efficiency bandwidth of up to 6:1 or up to 12:1, independently of the time delay or phase delay between the two antennas. In certain embodiments, the first and second antennas may be configured to transmit or receive signals over an efficiency bandwidth of up to 6:1 or up to 12:1, independently of the spatial sector in which the radio signal is transmitted or received.

[0149] In certain embodiments, the weight of the dielectric unit included in the antenna 500 is 0.8 to 1.4 kg / m 3 This may be the cube of the lowest operating wavelength at which the return loss of antenna 500 achieves or exceeds 6 dB. In certain embodiments, when operating without an outer ground plane, the weight of the dielectric unit is 1.5 to 2.8 kg / m 3This can be the result of multiplying the return loss of antenna 500 by the cube of the lowest operating wavelength at which it achieves or exceeds a return loss of 6 dB. The weight of the dielectric unit can be calculated from the dimensions of the antenna and the specific gravity of the material on which the dielectric unit is formed. In certain lightweight embodiments, the dielectric unit is 0.55 to 1.1 kg / m 3 The weight may be the weight multiplied by a multiple of the cube of the lowest operating wavelength at which the return loss of antenna 500 achieves or exceeds 6 dB. In certain lightweight embodiments, without an outer ground plane, the weight of the dielectric unit is 1-2.1 kg / m 3 This could be the result of multiplying the return loss of antenna 500 by the cube of the lowest operating wavelength at which it achieves or exceeds a return loss of 6 dB.

[0150] Figure 8A shows the geometric shape and features of antenna 800 in a two-dimensional diagram. Antenna 800 has the same topology as antenna 200, but has different physical dimensions, and in particular has smaller longitudinal dimensions due to its thin form factor. Antenna 800 is antenna K2 (<λ L / 5) relative to the antenna height (<λ L Lower the diameter (<λ) ( / 6) and the same diameter (<λ L Maintain the / 6) position. As will be discussed further below, lowering the antenna height of antenna 800 increases the beam scan at high frequencies (e.g., 4-6 fL) and reduces the on-horizon gain at these frequencies.

[0151] Figure 8A shows a cross-sectional view of antenna 800 comprising a conductive surface and a conductive mass. As shown in Figure 8A, antenna 800 is azimuthally uniform. A perspective view of antenna 800 corresponding to the cross-sectional view in Figure 8A can be generated by rotating the cross-sectional view in Figure 8A with respect to the radial symmetry axis 850.

[0152] The antenna 800 may be formed from a dielectric mass 810. As shown in Figure 8A, the dielectric mass 810 may have multiple surfaces, including a first radial inner surface 820, a non-conductive aperture surface 830, an inner ground surface, one or more edges 840A, 840B, and a base. The antenna 800 may be mated to a transmission line 835. To facilitate reference to various physical features and radio performance characteristics (particularly the radiation pattern), Figure 8A also shows the radiation symmetry axis 850 located at the radiation center of the antenna 800, the azimuthal plane 860, and the XYZ coordinate system.

[0153] As shown in Figure 8A, the dielectric mass 810 is azimuthally uniform (without variation according to φ), as can be seen when a cross-section is taken in an arbitrary elevation plane (θ-r plane) to obtain the diagram in Figure 8A. Rotating the cross-sectional view in Figure 8A about the radial symmetry axis 850 yields a three-dimensional dielectric mass 810 in which each face in the three-dimensional view has multiple surfaces corresponding to the curves in the cross-sectional view in Figure 8A. The dielectric mass 810 can be radially symmetric or azimuthally uniform with respect to the radial symmetry axis 850. The dielectric mass 810 terminates radially inward at the first radial inner surface 820. The dielectric mass 810 terminates radially outward at the non-conductive opening surface 830. The dielectric mass 810 terminates at the longitudinal maximum of one or more edges 840A. Figure 8A shows one edge 840A at the longitudinal maximum of the dielectric mass 810. The dielectric mass 810 terminates at its longitudinal minimum at the base. The dielectric mass 810 also has an inner ground surface extending radially outward from its base to one or more edges 840B or nonconductive opening surface 830.

[0154] In certain embodiments, the dielectric mass 810 has a maximum radius determined by the maximum radial dimension of the non-conductive opening surface 830. In certain embodiments, the dielectric mass 810 has a maximum height determined by the longitudinal distance between its base at its minimum longitudinal portion and its edge 840A at its maximum longitudinal portion. As shown in Figure 8A, the maximum radius of the dielectric mass 810 is λ L The height of the dielectric block 810 is λ, and does not exceed / 12. L Do not exceed / 6.

[0155] The first radial inner surface 820 may have the same or similar configuration, features, interface, parameters, or functions as the first radial inner surface 120 on the dielectric mass. The non-conductive aperture surface 830 may have the same or similar configuration, features, interface, parameters, or functions as the non-conductive aperture surface 130 on the dielectric mass. The inner ground surface of the dielectric 810 may have the same or similar configuration, features, interface, parameters, or functions as the inner ground surface 140 on the dielectric mass. One or more edges 840A, 840B may have the same or similar configuration, features, interface, parameters, or functions as the edges 150A, 150B on the dielectric mass. Note that the size and dimensions of the first radial inner surface 820, the non-conductive aperture surface 830, one or more edges 840A, 840B, the inner ground surface, and the base of the dielectric mass 810 correspond to antenna 800 shown in Figure 8A, not antenna 200.

[0156] The radial symmetry axis 850 defines the Z-axis, and with respect to the Z-axis, the dielectric mass 810 (and antenna 800) are azimuthally uniform or radially symmetric. The azimuthal plane 860 defines the radial horizon (θ=90°). In certain embodiments, the azimuthal plane 860 may also define an azimuthal plane (θ=90°, XY) corresponding to the external ground plane.

[0157] The dielectric mass 810 may be formed from any fabrication process, material, or composition of material described herein with respect to other dielectric masses disclosed herein, which conform to the topology of the dielectric mass 810 shown in Figure 8A.

[0158] The first radiator 805 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions in the antenna as the first radiator 205, except that the size and dimensions of the first radiator 805 correspond to antenna 800 instead of antenna 200. The first radiator 805 may be formed in the same or similar manner, operation, steps, parameters, and principles as the first radiator 205, and from the same or similar materials as the first radiator 205.

[0159] The internal ground 815 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as the internal ground 210 in the antenna, except that the size and dimensions of the internal ground 815 correspond to antenna 800 rather than antenna 200. As shown in Figure 8A, the internal ground 815 does not extend beyond the minimum longitudinal portion of the dielectric block 810, so that the height of antenna 800 is the same as the height of the dielectric block 810. The internal ground 815 may be formed in the same or similar manner, operation, steps, parameters, and principles as the internal ground 210, and from the same or similar material as the internal ground 210.

[0160] The external ground 825 in the antenna may have the same or similar structure, components, elements, configuration, features, interfaces, parameters, or functions as the external ground 220. The transmission line 835 may have the same or similar structure, components, elements, configuration, features, interfaces, parameters, or functions as the transmission line 230, and may be formed of the same or similar material as the transmission line 230.

[0161] Figures 8B and 9 show the radiation pattern and return loss over a 6:1 bandwidth (1–6 fL), as well as the time-domain performance of antenna 800. 6 This summarizes the performance of the product. 7 . 6 The performance shown in Figures 6 and 7 is the same as the radius (≤λ) of the dielectric mass. L This relates to antenna 500 equipped with a ground plane having a 20-degree angle ( / 20). 7 The performance shown in Figures 8B to 9 is the same as the radius (≤λ) of the dielectric mass. L This relates to antenna 800 equipped with a ground plane having a 12-degree angle ( / 12).

[0162] Figure 8B shows the return loss of antenna 800. The return loss of antenna 800 in Figure 8B is 10 dB or more over the efficiency bandwidth of 1.5–6 fL and 6 dB or more over the efficiency bandwidth of 1.33–6 fL. Although not shown in Figure 8B, antenna 800 maintains a return loss of over 10 dB up to 12 fL (i.e., 1.5 fL–12 fL). Although not shown in Figure 8B, the return loss of antenna 800 substantially achieves or exceeds 9 dB over the efficiency bandwidth of 1.5–12 fL, regardless of the size of the ground plane on which antenna 800 is placed. For all ground plane sizes, the return loss is substantially 9 dB or more over at least an 8:1 bandwidth (1.5–12 fL). The ground plane size has virtually no effect on the return loss performance above 2 fL (i.e., the return loss above 2 fL remains substantially 10 dB or more for all ground sizes).

[0163] Antenna 800 is unaffected by placement up to a return loss threshold of 9 dB above 1.5 fL. The size of the ground plane does not affect the return loss beyond a 9 dB threshold at frequencies above 2 fL, and the return loss is effectively 10 dB or more at frequencies above 1.5 fL, regardless of the size of the ground plane.

[0164] Figure 9 shows the radiation pattern of antenna 800 in the main cross-section at various frequencies. Figures 9A and 9B show the radiation pattern of antenna 800 maintaining two modes: one radiating a beam with substantially uniform gain at azimuth angles including the radiation horizon ("horizontal beam"), and the other radiating a conical beam at an elevation angle (θ) of 30° from the radiation axis of symmetry. Although not shown in Figures 9A and 9B, antenna 800 maintains both the horizontal and conical beams over a pattern bandwidth of at least 4.5:1 (1–4.5 fL). Figures 9C and 9D show the radiation pattern in the azimuth plane (XY, θ=90°) from 2–6 fL. The gain in the azimuth plane at 1.5 fL is substantially uniform from 1.8–2.1 dBi. However, the azimuth plane pattern of antenna 800 is substantially uniform over a 4:1 pattern bandwidth (1.5 to 6 fL), with a maximum variation of ±2 dB at 5.5 fL. Figures 9E and 9F show the radiation pattern from 2 to 6 fL at an elevation angle θ = 26° from the radiation symmetry axis. The gain at the θ = 26° cross-section at 1 fL is uniform at -0.8 dBi, and at 1.5 fL it is substantially uniform at -1.2 to -1.3 dBi. Antenna 800 maintains a conical beam from 1 to 6 fL.

[0165] Table 5 summarizes the fidelity of radio signals across different IBWs in the horizontal beam of Antenna 800. Antenna 800 can instantaneously transmit or receive radio signals over IBWs of at least 4:1 (1–4 fL) in the horizontal beam. Antenna 800 can also instantaneously transmit or receive radio signals over IBWs of up to 3 fL in various bandwidths in the horizontal beam. Antenna 800 can also instantaneously transmit or receive radio signals over bandwidths of up to 6:1 by instantaneously transmitting or receiving signals in one or more instantaneous frequency bands, each having at least the lowest operating frequency IBW.

[0166] [Table 5]

[0167] Table 6 summarizes the fidelity of the antenna 800 for radio signals across different IBWs in a conical beam. Although not shown in Table 6, the fidelity of the antenna 800 in a 1 fL bandwidth (e.g., 1–2 fL, 5–6 fL) exceeds 90%. The antenna 800 can instantaneously transmit or receive radio signals over IBWs up to 5:1 (1.5–7.5 fL) in a conical beam. The antenna 800 can also instantaneously transmit or receive radio signals over IBWs up to 6 fL (1.5–7.5 fL) in a conical beam. The antenna 800 can also instantaneously transmit or receive radio signals over bandwidths up to 12:1 by instantaneously transmitting or receiving signals in one or more instantaneous frequency bands, each having at least the lowest operating frequency IBW.

[0168] [Table 6]

[0169] Antenna 800 has substantially the same pattern and fidelity characteristics as those described in Tables 5 and 6 and Figure 9, even without an outer ground plane. λ L A ground with a radius of 12 lowers the minimum operating frequency at which return losses of 10 dB and 6 dB are achieved, but has little effect on fidelity, pattern, or IBW. Therefore, placing the antenna 800 or a variation thereof on a larger external ground plane can extend the minimum operating frequency while maintaining substantially the same pattern and fidelity performance as described herein.

[0170] Figures 10A and 10B show the geometric shape and features of antenna 1000 in two perpendicular cross-sectional views passing through the center of antenna 1000, each comprising a conductive surface and a conductive mass. In certain embodiments, the dielectric mass (and any corresponding dielectric unit or antenna) may be scaled in one or more radial dimensions. In certain embodiments, scaling may improve directivity in the direction of short radiation axes or surfaces (axes or surfaces with smaller scaling factors) or long radiation axes or surfaces (axes or surfaces with larger scaling factors). Stronger directivity in a particular direction may improve antenna performance in fixed point-to-point communications or other applications where the position of a transmitter or receiver can be determined. The antenna 1000 shown in Figures 10A and 10B has scaling factors sx = 0.8 (i.e., the radial dimension of the azimuthally uniform dielectric mass is reduced by 20% in the X dimension) and sy = 0.4 (i.e., the radial dimension of the azimuthally uniform dielectric mass is reduced by 60% in the Y dimension), such that the radius of the antenna 1000 in the X dimension is twice the radius of the antenna 1000 in the Y dimension. Therefore, the dielectric unit 1010 and the antenna 1000 are neither azimuthally uniform nor radially symmetric, but are symmetric with respect to the ZX and ZY planes that contain the axis of symmetry.

[0171] Antenna 1000 may be formed from a dielectric mass 1010. As shown in Figures 10A and 10B, the dielectric mass 1010 may have multiple surfaces, including a first radial inner surface 1020, a nonconductive aperture surface 1030, an inner ground surface, one or more edges 1040A, 1040B, and a base. Antenna 1000 may be mated to a transmission line 1035. To facilitate reference to various physical features and radio performance characteristics (particularly radiation pattern), Figures 10A and 10B also show the axis of symmetry 1050 located at the radiation center of antenna 1000, the azimuthal plane 1060, and the XYZ coordinate system.

[0172] As shown in Figures 10A and 10B, the dielectric mass 1010 is symmetric with respect to the axis of symmetry 1050. The dielectric mass 1010 is a three-dimensional dielectric mass having multiple surfaces, each face in the three-dimensional view corresponding to one or more curves in the cross-sectional views of Figures 10A and 10B. The dielectric mass 1010 terminates radially inward at the first radial inner surface 1020. The dielectric mass 1010 terminates radially outward at the non-conductive opening surface 1030. The dielectric mass 1010 terminates at its longitudinal maximum at one or more edges 1040A. Figures 10A and 10B show one edge 1040A at the longitudinal maximum of the dielectric mass 1010. The dielectric mass 1010 terminates at its longitudinal minimum at the base. In certain embodiments, the base of the dielectric mass 1010 may be unscaled. By not scaling the base of the dielectric block 1010, it may be easier to interface it with the transmission line 1035. The dielectric block 1010 also has an inner ground surface on its radially outer side that extends from the base to one or more edges 1040B or nonconductive opening surface 1030.

[0173] In certain embodiments, the dielectric mass 1010 has a maximum radius determined by the maximum radial dimension of the non-conductive aperture surface 1030 in the long-radiating plane. As shown in Figures 10A and 10B, the maximum radius of the dielectric mass 1010 lies in the ZX plane of Figure 10A (i.e., the major-radius plane of the dielectric mass 1010). In certain embodiments, the dielectric mass 1010 has a minor radius determined by the maximum radial dimension of the non-conductive aperture surface 1030 in the short-radiating plane (e.g., the ZY plane of Figure 10B). In certain embodiments, the dielectric mass 1010 has a maximum height determined by the longitudinal distance between the base at its minimum longitudinal end and the edge 1040A at its maximum longitudinal end. As shown in Figure 10A, the maximum (or major) radius of the dielectric mass 1010 is λ L It does not exceed / 12. As shown in Figure 10B, the minor radius of the dielectric block 1010 is λ L The height of dielectric block 1010 is λ. L Do not exceed / 5.

[0174] The first radial inner surface 1020 may have the same or similar configuration, features, interface, parameters, or functions as the first radial inner surface 120 on the dielectric mass, except that the first radial inner surface 1020 is symmetric rather than azimuthally uniform or radially symmetric. The nonconductive aperture surface 1030 may have the same or similar configuration, features, interface, parameters, or functions as the nonconductive aperture surface 130 on the dielectric mass, except that the nonconductive aperture surface 1030 is symmetric rather than azimuthally uniform or radially symmetric. The inner ground surface of the dielectric 1010 may have the same or similar configuration, features, interface, parameters, or functions as the inner ground surface 140 on the dielectric mass, except that the inner ground surface of the dielectric 1010 is symmetric rather than azimuthally uniform or radially symmetric. One or more edges 1040A, 1040B may have the same or similar configuration, features, interfaces, parameters, or functions on the dielectric mass as edges 150A, 150B, except that one or more edges 1040A, 1040B are symmetric rather than azimuthally uniform or radially symmetric. Note that the size and dimensions of the first radial inner surface 1020, the nonconductive aperture surface 1030, one or more edges 1040A, 1040B, the inner ground surface, and the base of the dielectric mass 1010 correspond to antenna 1000 shown in Figures 10A and 10B, not antenna 200.

[0175] The axis of symmetry 1050 defines the Z-axis at the center of the antenna 1000, and the dielectric mass 1010 (and antenna 1000) are symmetric with respect to the center of the antenna 1000. The azimuth plane 1060 defines the radiation horizon (θ=90°). In certain embodiments, the azimuth plane 1060 may also define an azimuth plane (θ=90°, XY) corresponding to the external ground plane.

[0176] The dielectric mass 1010 may be formed from any fabrication process, material, or composition of material described herein with respect to other dielectric masses disclosed herein, which conform to the symmetric topology of the dielectric mass 1010 shown in Figures 10A and 10B.

[0177] The first radiator 1005 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions in the antenna as the first radiator 205, except that the size and dimensions of the first radiator 1005 correspond to antenna 1000 instead of antenna 200. The first radiator 1005 may be formed in the same or similar manner, operation, steps, parameters, and principles as the first radiator 205, and from the same or similar materials as the first radiator 205.

[0178] The internal ground 1015 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as the internal ground 210 in the antenna, except that the size and dimensions of the internal ground 1015 correspond to antenna 1000 rather than antenna 200, and may be formed from the same or similar material as the internal ground 210. As shown in Figures 10A and 10B, the internal ground 1015 extends beyond the longitudinal minimum of the dielectric block 1010 (as shown where the internal ground 1015 interfaces with the dielectric of the transmission line 1035) so that the height of antenna 1000 exceeds the height of the dielectric block 1010. In certain embodiments, the internal ground 1015 may not extend longitudinally beyond the longitudinal minimum of the dielectric block 1010 so that the heights of antenna 1000 and dielectric block 1010 are the same. The internal ground 1015 may be formed according to the same or similar methods, operations, steps, parameters, and principles as the internal ground 210.

[0179] The external ground 1025 in the antenna may have the same or similar structure, components, elements, configuration, features, interface, parameters, or functions as the external ground 220. The transmission line 1035 may have the same or similar structure, components, elements, configuration, features, interface, parameters, or functions as the transmission line 230.

[0180] Figures 11 and 12 summarize the overall performance of Antenna 1000, including its radiation pattern, return loss, and time-domain performance over a 6:1 bandwidth (1 to 6 fL).8 . 8 The performance figures shown in Figures 11 and 12 pertain to antenna 1000 without an external ground plane. By coupling antenna 1000 to a ground plane exceeding its radial dimension (in X or Y), it is possible to improve the return loss at low frequencies and increase the peak gain while maintaining low distortion performance.

[0181] Figure 11A shows the return loss of antenna 1000. The return loss of antenna 1000 in Figure 11A is greater than 10 dB over an efficiency bandwidth of 1.5–6 fL. Although not shown in Figure 11A, antenna 1000 maintains a return loss of more than 10 dB up to 12 fL (i.e., 1.5 fL–12 fL). Also not shown in Figure 11A, the return loss of antenna 1000 exceeds 8 dB over an efficiency bandwidth of 1.5–12 fL, regardless of the size of the ground plane on which antenna 1000 rests. For all ground plane sizes, the return loss is greater than 8 dB over at least an 8:1 bandwidth (1.5–12 fL). The ground plane size has virtually no effect on return loss performance above 2 fL (i.e., the return loss above 2 fL remains substantially greater than 8 dB for all ground sizes).

[0182] Antenna 1000 is unaffected by placement up to a return loss threshold of 8 dB above 1.5 fL. The size of the ground plane has no substantial effect on the return loss beyond 8 dB at frequencies above 2 fL, and the return loss is substantially 8 dB or more at frequencies above 1.5 fL regardless of the size of the ground plane. In certain embodiments, shaping the ground plane to remove surface waves or edge diffraction, or treating the edges or surfaces (e.g., metasurfaces or integrated filters), can achieve a return loss of 10 dB in antenna 1000 over a 6:1 bandwidth for any ground plane size.

[0183] Figures 11B and 11C show exemplary time-domain responses of antenna 1000. Figure 11B shows the time-domain response of antenna 1000 for radio signals transmitted and received on a horizontal beam (θ=90°) covering 2–6 fL. Figure 11C shows the time-domain response of antenna 1000 for radio signals transmitted and received on a conical beam (θ=20°) covering 1.5–6 fL. Table 7 summarizes the fidelity of antenna 1000 for radio signals across different IBWs on the horizontal beam. Table 7 summarizes the fidelity at both azimuth angles φ=0° and φ=90°, due to the lack of azimuth uniformity in the horizontal beam of antenna 1000. The fidelity at φ=90° is most noteworthy because the gain is maximum at that angle, but antenna 1000 maintains similarly good fidelity in the φ=0° direction. Antenna 1000 can instantaneously transmit or receive radio signals over an IBW (1 to 6 fL) of at least 6:1 in the horizontal beam. Antenna 1000 can also instantaneously transmit or receive radio signals over an IBW of up to 5 fL in various bandwidths in the horizontal beam. Antenna 1000 can also instantaneously transmit or receive radio signals over a bandwidth of up to 6:1 by instantaneously transmitting or receiving signals in one or more instantaneous frequency bands, each having an IBW of at least the lowest operating frequency.

[0184] [Table 7]

[0185] Table 8 summarizes the fidelity of the antenna 1000 for radio signals across different IBWs in a conical beam. Although not shown in Table 8, the fidelity of the antenna 1000 exceeds 90% in the 1 fL bandwidth (e.g., 1-2 fL, 5-6 fL) and the 1.5 fL bandwidth (e.g., 1.5-3 fL). The antenna 1000 can instantaneously transmit or receive radio signals over IBWs up to 6:1 (1-6 fL) in a conical beam. The antenna 1000 can also instantaneously transmit or receive radio signals over IBWs up to 5 fL (1-6 fL) in a conical beam. The antenna 1000 can also instantaneously transmit or receive radio signals over bandwidths up to 6:1 by instantaneously transmitting or receiving signals in one or more instantaneous frequency bands, each having an IBW of at least the lowest operating frequency.

[0186] [Table 8]

[0187] Figure 12 shows the radiation pattern of antenna 1000 in its main cross-section at various frequencies. Figures 12A and 12B show the radiation pattern of antenna 1000 in the ZY plane (φ=90°). Antenna 1000 maintains two modes in the ZY plane over a 4:1 pattern bandwidth, one including a radiation horizontal line ("horizontal beam"), and the other radiating a conical beam around an elevation angle (θ) of 20° from the radiation axis of symmetry. The horizontal beam of antenna 1000 is not uniform in azimuthal angle (in contrast to other embodiments) due to the lack of radiation symmetry in antenna 1000. Figures 12C and 12D show the radiation pattern in the ZX plane (φ=0°). As shown in Figures 12C and 12D, antenna 1000 maintains a conical beam in the ZX plane over a 4:1 pattern bandwidth (1.5–6 fL), but maintains a horizontal beam in a narrower bandwidth due to the lack of radiation symmetry in antenna 1000. Figures 12E and 12F show the radiation patterns for 2–6 fL along the horizontal line (at an elevation angle θ=90° from the radial symmetry axis). The gain of antenna 1000 at 1.5 fL along the horizontal line is substantially uniform, ranging from 1.1 to 1.3 dBi. Figures 12G and 12H show the radiation patterns for 2–6 fL along the conical beam (at an elevation angle θ=20° from the radial symmetry axis). The gain of antenna 1000 along the conical beam at 1.5 fL (i.e., the θ=20° cross-section) varies from -3.7 dBi at φ=0° to -4.4 dBi at φ=90°.

[0188] Antenna 1000 has an outer ground plane and has substantially the same pattern and fidelity characteristics as those described in Figures 11 and 12 and Tables 7 and 8. The outer ground lowers the minimum operating frequency at which return losses of 10 dB and 6 dB are achieved, but has little effect on fidelity, pattern, or IBW. Therefore, placing antenna 1000 or its variants on a larger outer ground plane can extend the minimum operating frequency while maintaining substantially the same pattern and fidelity performance as described herein.

[0189] Figures 13A to 13C show the geometric shape and features of antenna 1300 in perspective and cross-sectional views. The cross-sectional views in Figures 13B and 13C are taken through the center of antenna 1300 shown in Figure 13A. Figure 13B is a cross-sectional view of antenna 1300 with a conductive surface and conductive mass, and Figure 13C is the same cross-sectional view without the conductive surface and conductive mass. Although Figures 13B and 13C show cross-sections in the ZY plane, the same figures can be obtained in cross-sections in any elevation plane (i.e., in any elevation plane θ-r) passing through the center of antenna 1300.

[0190] The dielectric block 1310 may have multiple surfaces, including a non-conductive aperture surface 1320, a first radial inner surface 1330, a second radial inner surface 1340, one or more feeding surfaces 1350, and one or more edges 1360A, 1360B. The dielectric block 1310 can be mated to a transmission line 1355. To facilitate reference to various physical features and radio performance characteristics (particularly radiation patterns), Figures 13B and 13C also show an azimuthal plane 1370, a radiation symmetry axis 1380 located at the radiation center of the dielectric block 1310 (and antenna 1300), and an XYZ coordinate system.

[0191] As shown in Figure 13, the dielectric mass 1310 is azimuthally uniform (without variation according to φ) as can be seen when a cross-section is taken in an arbitrary elevation plane (θ-r plane), yielding the diagrams in Figures 13B and 13C. When the cross-sectional diagrams in Figures 13B and 13C are rotated about the radial symmetry axis 1380, a three-dimensional dielectric mass 1310 is obtained, as shown in Figure 13A, in which each face in the three-dimensional diagram has multiple surfaces corresponding to the curves in the cross-sectional diagrams in Figures 13B and 13C. The dielectric mass 1310 can be radially symmetric or azimuthally uniform with respect to the radial symmetry axis 1380. The dielectric mass 1310 terminates radially inward at a first radial inner surface 1330, a second radial inner surface 1340, and one or more power supply surfaces 1350. The dielectric mass 1310 terminates radially outward at a non-conductive aperture surface 1320. The dielectric block 1310 terminates at its longest longitudinal portion at one or more edges 1360A. Figure 13 shows one edge 1360A at the longest longitudinal portion of the dielectric block 1310. The dielectric block 1310 also terminates at its shortest longitudinal portion at one or more edges 1360B.

[0192] In certain embodiments, the dielectric mass 1310 has a maximum radius determined by the maximum radial (ρ) dimension of the nonconductive opening surface 1320. In certain embodiments, the dielectric mass 1310 has a maximum height determined by the longitudinal (Z) distance between the longest longitudinal portion (edge ​​1360A in Figure 13C) and the shortest longitudinal portion (edge ​​1360B in Figure 13C) of the dielectric mass 1310.

[0193] As shown in Figure 13, the dielectric mass 1310 is composed of a single, uniform dielectric material. In certain embodiments, the dielectric mass may contain one or more cavities that do not contain dielectric material. For example, certain spaces in the dielectric mass may be formed by additive manufacturing, leaving other spaces as cavities during the additive manufacturing process. In certain embodiments, the dielectric mass may contain one or more drainage holes to empty or backfill one or more cavities. In certain embodiments, one or more drainage holes may be radially symmetric, azimuthally uniform, or symmetric. For example, to maintain the structural integrity of the dielectric mass, N drainage holes, each 360 / N degrees apart in azimuthal, may help empty N separate cavities. In certain embodiments, the presence of one or more cavities in the dielectric mass does not affect the continuity of conductive surfaces in the dielectric mass. For example, the dielectric unit may include one or more cavities and drainage holes that do not intersect with the first radial inner surface 1330, the second radial inner surface 1340, the power supply surface 1350, or any other surface that can form a base for a conductive surface.

[0194] In certain embodiments, the dielectric mass may be composed of multiple dielectric materials. For example, one or more cavities may be filled with dielectric material. Including one or more cavities in the dielectric mass can reduce weight, control the effective dielectric constant of the antenna, and suppress or promote radiation in different modes. In certain embodiments, the effective dielectric constant may be calculated as the volume-weighted average of the dielectric constants of one or more materials in the dielectric mass. For example, a dielectric mass formed from a material having a dielectric constant of 2.1 and having air cavities (dk=1) in 50% of its volume has an effective dielectric constant dk e =(0.5)(2.1)+(0.5)(1)=1.55. In certain embodiments, one or more cavities may facilitate certain functions in the antenna radiation pattern, such as radially symmetric, azimuthally uniform, or symmetric, with an azimuthally uniform beam, or greater directivity in a particular direction.

[0195] In certain embodiments, the dielectric mass may be formed of one or more materials having a dielectric constant of 1.03 to 3.6. In certain embodiments, the dielectric unit may have a dielectric constant of 1.4 to 3.6. In certain embodiments, in order to improve structural integrity, the dielectric unit may have a dielectric constant of 1.8 to 3.1.

[0196] In certain embodiments, the dielectric mass may be formed of a material having a specific gravity of 1.02 to 1.38. In certain embodiments, the dielectric mass may be formed of a plurality of materials including a first material having a specific gravity of 1.02 to 1.38 and a second material having a specific gravity of 0.03 to 0.2.

[0197] The non-conductive opening surface 1320 located on the radially outer side of the dielectric mass 1310 determines the radially maximum portion of the dielectric mass 1310. As shown in FIGS. 13B and 13C, the non-conductive opening surface 1320 extends longitudinally between two edges 1360A, 1360B. The dielectric mass 1310 terminates at the non-conductive opening surface 1320 in free space. In certain embodiments, the non-conductive opening surface 1320 includes a convex surface, a concave surface, or both a convex surface and a concave surface. Although not shown in FIG. 13B, in certain embodiments, the radially minimum portion of the non-conductive opening surface 1320 may exceed the radially maximum portion of the first radiator 1305 or the second radiator 1315.

[0198] The first radial inner surface 1330, located on the radially inward side of the dielectric mass 1310, may extend longitudinally from one or more power supply surfaces 1350 to the maximum longitudinal portion of the dielectric mass 1310 (e.g., edge 1360A in Figure 13C). In certain embodiments without edges 1360A, 1360B, the first radial inner surface 1330 may extend radially from one or more power supply surfaces 1350 to the maximum radial portion of the dielectric mass 1310 (e.g., the maximum radial portion of the nonconductive opening surface 1320 in Figure 13B). In certain embodiments, the first radial inner surface 1330 includes a convex surface, a concave surface, or both convex and concave surfaces. In certain embodiments, the space on the radially inward side of the first radial inner surface 1330 is a cavity (e.g., free space or air). As will be discussed further below, in certain embodiments, a conductive surface (e.g., a metallic radiator) or a dielectric structure (e.g., a dielectric base) may be inserted into the cavity. In certain embodiments, the conductive surface may be fitted into the first radial inner surface 1330 during the fabrication of the antenna 1300.

[0199] A second radial inner surface 1340 located on the radially inward side of the dielectric mass 1310 may extend longitudinally from one or more power supply surfaces 1350 to the longitudinal minimum of the dielectric mass 1310. In certain embodiments without edges 1360A, 1360B, the second radial inner surface 1340 may extend radially from one or more power supply surfaces 1350 to the radial maximum of the dielectric mass 1310 (e.g., the radial maximum of the nonconductive opening surface 1320 in Figure 13B). In certain embodiments, the second radial inner surface 1340 includes a convex surface, a concave surface, or both convex and concave surfaces. In certain embodiments, the space on the radially inward side of the second radial inner surface 1340 is a cavity (e.g., free space or air). As will be discussed further below, in certain embodiments, a conductive surface (e.g., a metallic radiator) or a dielectric structure (e.g., a dielectric base) may be inserted into the cavity. In certain embodiments, the conductive surface can be fitted into the second radial inner surface 1340 during the fabrication of the antenna 1300.

[0200] One or more feeding surfaces 1350 located on the radially inward side of the dielectric mass 1310 may extend radially and longitudinally from the radial minimum of the dielectric mass 1310 to the first radial inner surface 1330, the second radial inner surface 1340, or both. In certain embodiments, the feeding surface 1350 may extend only longitudinally between the first radial inner surface 1330 and the second radial inner surface 1340. In certain embodiments, the feeding surface 1350 may extend only radially between the first radial inner surface 1330 and the second radial inner surface 1340. In certain embodiments, one or more feeding surfaces 1350 may be mated to a transmission line. For example, as shown in Figure 13C, one or more feeding surfaces 1350 may be mated to a coaxial connector or cable, such as a bulkhead, screw-in, or flanged coaxial connector or cable.

[0201] The dielectric mass 1310 may have one or more edges 1360A, 1360B. As shown in Figure 13C, the dielectric mass 1310 includes one edge 1360A at the maximum longitudinal portion of the dielectric mass 1310 and one edge 1360B at the minimum longitudinal portion of the dielectric mass 1310. In certain embodiments, the edges 1360A, 1360B may be included in the dielectric mass 1310 to accommodate manufacturing tolerances or to provide a flat surface (e.g., a flat surface parallel to the XY plane) for mating with other structures, as will be discussed further below. In certain embodiments, the dielectric mass 1310 may not include the edges 1360A, 1360B.

[0202] As shown in Figure 13B, the azimuth plane 1370 defines the radial horizon (θ=90°). In certain embodiments, the azimuth plane 1370 may also define an azimuth plane (θ=90°, XY) corresponding to the external ground plane.

[0203] The radial symmetry axis 1380 defines the Z-axis, and with respect to the Z-axis, the dielectric mass 1310 is azimuthally uniform or radially symmetric. An azimuthally uniform structure does not change with respect to the azimuthal angle (φ). The dielectric mass 1310 is azimuthally uniform as shown in Figure 13. In certain embodiments, the dielectric mass 1310 may be radially symmetric to achieve specific RF performance characteristics or to facilitate a specific manufacturing method.

[0204] In certain embodiments, a dielectric unit may be formed from a dielectric mass 1310. To form the dielectric unit, a first conductive surface may be positioned on a first radial inner surface 1330, a second conductive surface may be positioned on a second radial inner surface 1340, or both. Conductive surfaces may also be positioned on one or more feeding surfaces 1350 as needed to provide electrical coupling to a transmission line. In certain embodiments, the first or second conductive surface may also be positioned on one or more edges 1360B. In certain embodiments, by forming a dielectric mass (and dielectric unit) as a single integrated whole, previously unattainable dielectric compositions and effective RF characteristics are realized for achieving the radio performance disclosed herein.

[0205] The dielectric block 1310 may be formed from any fabrication process, material, or composition of material described herein with respect to other dielectric blocks disclosed herein, which conform to the topology of the dielectric block 1310 shown in Figure 13. The dielectric block 1310 may be formed by additive manufacturing, machining, injection molding, or similar processes. For example, the dielectric block 1310 may be formed from Ultem® material in a fused deposition modeling (FDM) process. As another example, the dielectric block 1310 may be formed from ABS in a stereolithography (SLA) process. As yet another example, the dielectric block 1310 may be formed by machining Teflon.

[0206] The surface of the dielectric mass 1310 may be epoxy coated, painted, or treated for various applications. In certain embodiments, the non-conductive aperture surface 1320 may be painted. For example, the non-conductive aperture surface 1320 may be painted white, light blue, gray, or a combination of colors to make the antenna less visible on an airborne or sea platform. In certain embodiments, the surface of the dielectric mass 1310 may be treated to reduce the adhesion of water, dirt, or other substances that may affect structural integrity, service life, or radio performance. In certain embodiments, the surface of the dielectric mass 1310 may be treated to facilitate the fabrication of the antenna. For example, the first radial inner surface 1330 may be sandblasted or chemically etched to facilitate the adhesion of the first conductive surface to the first radial inner surface 1330.

[0207] In certain embodiments, the dielectric mass 1310 (and any corresponding dielectric unit or antenna) may be scaled in one or more radial dimensions. In certain embodiments, scaling may improve directivity in the direction of short radiation axes or planes (axes or planes with smaller scaling factors) or long radiation axes or planes (axes or planes with larger scaling factors). For example, antenna 1300 may have scaling factors sx = 0.8 (i.e., the radial dimension of the azimuthally uniform dielectric mass is reduced by 20% in the X dimension) and sy = 0.4 (i.e., the radial dimension of the azimuthally uniform dielectric mass is reduced by 60% in the Y dimension), such that the radius of antenna 1300 in the X dimension is twice the radius of antenna 1000 in the Y dimension. In certain embodiments, antenna 1300 may be symmetric with respect to the ZX and ZY planes, which include the axis of symmetry.

[0208] Figure 13B shows a cross-sectional view of antenna 1300 comprising a dielectric block 1310. As shown, antenna 1300 also comprises a first radiator 1305, a second radiator 1315, a top hat 1325, a ground plane 1335, a first cavity 1365, and a second cavity 1375. As shown in Figure 13B, the first radiator 1305, the second radiator 1315, the top hat 1325, and the ground plane 1335 are conductive elements. Antenna 1300 can be electrically coupled to a transmission line 1345 via pin 1355 for transmitting and receiving RF energy.

[0209] As shown in Figures 13A and 13B, the maximum radius of antenna 1300 is λ L The maximum height of the antenna 200 is λ, and it does not exceed / 6. L It shall not exceed / 4. In certain embodiments, the maximum height of the antenna may be increased to shift the antenna's operating bandwidth to lower frequencies or to improve return loss at lower frequencies in the antenna's operating bandwidth. In certain embodiments, reducing the antenna height may improve transmission phase linearity across the antenna's operating bandwidth, thereby reducing distortion and increasing the fidelity of instantaneous broadband radio signals. In certain embodiments, the radius of the antenna may be adjusted to facilitate matching with the antenna or to achieve the antenna gain at a desired frequency.

[0210] The first radiator 1305 is located radially inward of the dielectric mass 1310 and presents a conductive surface on the first radial inner surface 1330. The first radiator 1305 may also present a conductive surface at one or more edges 1360A between the first radial inner surface 1330 and the non-conductive aperture surface 1320. The first radiator 1305 may also present a conductive surface at a pin extending from the transmission line to the antenna 1300. The first radiator 1305 may extend longitudinally from the feeding surface 1350 to the maximum longitudinal portion of the dielectric mass 1310 (e.g., edge 1360A in Figure 13C). In certain embodiments, the first radiator 1305 may extend from the central conductor of the transmission line (e.g., a pin extending from the transmission line) to the maximum longitudinal portion of the dielectric mass 1310. The first radiator 1305 may be azimuthally uniform or radially symmetric. In certain embodiments, the first radiator 1305 may be symmetrical. The first radiator 1305 may extend radially from the inner conductor of the transmission line to one or more edges 1360A of the dielectric mass 1310. In certain embodiments, the first radiator 1305 may extend to the maximum longitudinal radius of the dielectric mass 1310 (for example, to the nonconductive aperture surface 1320 in Figure 13B). In certain embodiments, the first radiator 1305 may include a convex surface, a concave surface, or both convex and concave surfaces.

[0211] In certain embodiments, the space on the radially inner side of the first radiator 1305 is a cavity (e.g., free space or air). In certain embodiments, a dielectric structure (e.g., a dielectric filler) may be inserted into the cavity on the radially inner side of the first radiator 1305.

[0212] The first radiator 1305 may be formed by machining, additive manufacturing, sintering, stamping, spraying, rolling, or deposition processes, or from one or more similar processes. For example, the first radiator 1305 may be machined or additive manufactured from a conductive material (e.g., copper or aluminum) such that the first radiator 1305 fills the entire space on the radially inward side of the first radial inner surface 1330. As another example, the first radiator 1305 may be formed without a conductive mass by depositing a first conductive surface on the first radial inner surface 1330. As yet another example, the first radiator 1305 may be formed without a conductive mass by stamping a conductive sheet and bonding it to the first radial inner surface 1330. In certain embodiments, forming the first radiator 1305 without a conductive mass may have the advantage of reducing the size and weight of the antenna 1300. In certain embodiments, the first radiator 1305 may be formed from a conductive mass to partially fill a cavity on the radially inward side of the first radial inner surface 1330. For example, the first radiator 1305 may be formed by stamping a conductive plate, or by machining or additively manufacturing a conductive material to a certain thickness and bonding it to the first radial inner surface 1330. Forming the first radiator 1305 to partially fill a cavity on the radially inward side of the first radial inner surface 1330 may have the advantage of presenting a conductive surface in the maximum longitudinal dimension of the antenna 1300 for mating, fastening, or coupling to other structures. For example, the first radiator 1305 may be formed with a radial thickness sufficient to facilitate conductive epoxy resin bonding or other bonding of a conductive top hat to the first radiator 1305. In another embodiment, the conductive top hat may be bonded to the first radiator 1305 via one or more edges 1360A. For example, a conductive surface may be positioned on the edge 1360A to maintain connections with both the first radiator 1305 and the top hat. Coupling the metal top hat to the first radiator 1305 may have the advantage of isolating any cavities radially inside the first radiator 1305 from the external environment and preventing current from flowing radially inside the first radiator 1305.

[0213] In certain embodiments, the first radiator 1305 may be formed by arranging one or more conductive surfaces on a dielectric substrate. For example, the first radiator 1305 may be formed without a conductive mass by electrolytic deposition of copper onto the dielectric substrate. As another example, the first radiator 1305 may be formed by stamping one or more conductive sheets and fitting the stamped sheets onto the dielectric substrate. Forming the first radiator 1305 by arranging conductive surfaces on a dielectric substrate may have one or more advantages, including reducing the size and weight of the antenna, enhancing the structural integrity of the first radiator 1305, reducing RF loss by presenting a smooth conductive surface to the associated RF energy passing through the dielectric mass, and facilitating a non-selective process for presenting a conductive surface on the first radial inner surface 1330. For example, forming the first radiator 1305 on a dielectric substrate may allow conductive plating of the entire surface on the dielectric substrate without masking. The dielectric base in the first radiator 1305 may consist of any dielectric material discussed with respect to the dielectric mass 1310, or any dielectric material suitable for mating, depositing, and bonding conductive surfaces on the dielectric base.

[0214] In certain embodiments, the first radiator 1305 may be fitted into the first radial inner surface 1330 during the construction of the antenna. For example, the first radiator 1305 may be machined from a conductive material and bonded to the first radial inner surface 1330 with epoxy resin. As another example, the first radiator 1305 may be formed by electrolytic emission of a conductor onto a dielectric base, inserted into a cavity on the radially inward side of the first radial inner surface 1330, fitted into the first radial inner surface 1330, and secured by a dielectric mass and a metal top hat or dielectric top hat. The first radiator 1305 may be formed directly on the first radial inner surface 1330. For example, the first radiator 1305 may be formed by spraying a conductive ink or dispersion onto the first radial inner surface 1330.

[0215] In certain embodiments, the first radiator 1305 may be electrically coupled to a transmission line. For example, the first radiator 1305 may be soldered, welded, or joined to a pin extending from the center conductor of the transmission line. Alternatively, a pin extending from the center conductor of a coaxial connector may be press-fitted into the first radiator 1305. Coupled the first radiator 1305 to a transmission line excites an RF current in the first radiator 1305 over a wide bandwidth.

[0216] In certain embodiments, the first radiator 1305 may be fitted to or electrically coupled to a top hat. For example, the first radiator 1305 may be fixed within the dielectric mass 1310 by a dielectric top hat fastened to the dielectric mass 1310. In another example, the first radiator 1305 may be conductively bonded with epoxy resin to a conductive top hat that prevents current from flowing radially inside the first radiator 1305 in its maximum longitudinal dimension.

[0217] In certain embodiments, the maximum radial dimension of the first radiator 1305 may exceed the minimum radial dimension of the nonconductive aperture surface 1320 (for example, shown in Figure 13B). Reducing the minimum radial dimension of the nonconductive aperture surface 1320 may offer the advantages of thinning the dielectric mass 1310, reducing the weight of the antenna 1300, or increasing the operating bandwidth of the antenna 1300. In certain embodiments, the maximum radial dimension of the nonconductive aperture surface 1320 may exceed the maximum radial dimension of any edge 1360A on the first radiator 1305 and the dielectric mass 1310. Increasing the thickness of the dielectric mass 1310 may have the advantages of lowering the lowest operating frequency of the antenna 1300, improving the return loss of the antenna 1300 near the lowest operating frequency, or controlling the gain or azimuthal uniformity of the radiation pattern at a particular frequency.

[0218] The second radiator 1315 is located on the radially inner side of the dielectric block 1310 and presents a conductive surface to the second radially inner surface 1340. The second radiator 1315 may also present a conductive surface at one or more edges 1360B between the second radially inner surface 1340 and the non-conductive aperture surface 1320. The second radiator 1315 may extend longitudinally and radially from one or more feed surfaces 1350 to one or more edges 1360B or the non-conductive aperture surface 1320. In certain embodiments, the second radiator 1315 may extend from the outer conductor of a transmission line (e.g., the shield of a coaxial cable or connector) to the longitudinal minimum of the dielectric block 1310. The second radiator 1315 may be azimuthally uniform or radially symmetric. In certain embodiments, the second radiator 1315 may be symmetric. The second radiator 1315 may extend radially from the outer conductor of the transmission line to one or more edges 1360B of the dielectric block 1310. In certain embodiments, the second radiator 1315 may extend to the longitudinal maximum radius of the dielectric block 1310. In certain embodiments, the second radiator 1315 includes convex, concave, or both convex and concave surfaces. In certain embodiments, the second radiator 1315 may have the same maximum radius as the first radiator 1305. In certain embodiments, the second radiator 1315 may have a maximum radius that is greater than or less than the maximum radius of the first radiator 1305.

[0219] In certain embodiments, the space on the radially inner side of the second radiator 1315 is a cavity (e.g., free space or air). In certain embodiments, a dielectric structure (e.g., a dielectric filler) may be inserted into the cavity on the radially inner side of the second radiator 1315.

[0220] The second radiator 1315 may be formed according to the same or similar methods, operations, steps, parameters, and principles as the first radiator 1305, and may be assembled into the antenna 1300, or integrated into the antenna 1300, according to the same or similar methods, operations, steps, parameters, and principles as the first radiator 1305.

[0221] In certain embodiments, the second radiator 1315 may be electrically coupled to a transmission line. For example, the second radiator 1315 may be soldered, welded, or joined to the outer conductor of the transmission line. As another example, the conductive surface of the second radiator 1315 may function as the outer conductor of the transmission line (for example, the conductive surface of the second radiator 1315 may be mated to a dielectric "candlestick" extending from a coaxial connector). Coupled the second radiator 1315 to the transmission line excites an RF current in the second radiator 1315 over a wide bandwidth.

[0222] In certain embodiments, the second radiator 1315 may be mated to or electrically coupled to a ground plane. For example, the second radiator 1315 may be fixed within the dielectric block 1310 by a ground plane fastened to the dielectric block 1310. In another example, the second radiator 1315 may be conductively bonded with epoxy resin to a conductive ground plane that prevents current from flowing radially inside the second radiator 1315 in its minimum longitudinal dimension.

[0223] In antenna 1300, RF energy propagates between the first conductive surface presented by the first radiator 1305 and the second conductive surface presented by the second radiator 1315. The RF energy propagates between these two conductive surfaces from the transmission line through the dielectric block 1310 to the non-conductive aperture surface 1320 (transmission), and from the non-conductive aperture surface 1320 through the dielectric block 1310 back to the transmission line (reception).

[0224] In certain embodiments, the maximum radial dimension of the second radiator 1315 may exceed the minimum radial dimension of the nonconductive aperture surface 1320 (for example, shown in Figure 13B). In certain embodiments, the maximum radial dimension of the nonconductive aperture surface 1320 may exceed the maximum radial dimension of the second radiator 1315 and any edge 1360B on the dielectric mass 1310.

[0225] The top hat 1325 is a conductive surface located at the maximum longitudinal portion of the antenna 1300, as shown in Figure 13B. The top hat 1325 may extend from the radial symmetry axis 1380 to the maximum radial portion of the dielectric mass 1310. In certain embodiments, the top hat 1325 may extend beyond the maximum longitudinal portion of the dielectric mass 1310. In certain embodiments, the top hat 1325 may be thin enough so that the height of the antenna 1300 is approximately the same as the height of the dielectric mass 13. For example, the height of both the antenna 1300 and the dielectric mass 1310, including the top hat 1325, may be 0.22λ. L It may not exceed this value. The top hat 1325 can be electrically coupled to the first radiator 1305 and any conductive surface located on the edge 1360A at the maximum longitudinal portion of the dielectric surface 1310. In certain embodiments, the top hat 1325 may be a dielectric material rather than a conductive material.

[0226] The top hat 1325 can isolate the first radiator 1305 and any cavities located radially inside the first radiator 1305 from the external environment. In certain embodiments, the top hat 1325 can fix the first radiator 1305. For example, the top hat 1325 can be fastened, epoxy-bonded, screwed, or bolted to the dielectric mass 1310 to prevent the first radiator 1305 from moving longitudinally or radially. In certain embodiments, the top hat 1325 can be fixed to the dielectric mass 1310. In certain embodiments, the top hat 1325 can be fixed to the first radiator 1305. For example, the top hat 1325 can be fastened to the first radiator 1305, which is a machined copper mass, with one or more conductive screws or bolts.

[0227] In certain embodiments, the top hat 1325 may be integrated with the first radiator 1305. For example, the top hat 1325 and the first radiator 1305 may be machined from a single block of conductive material. In certain embodiments, the top hat 1325 may be part of a larger platform on which the antenna 1300 is mounted. For example, the top hat 1325 may be a conductive surface of a tower or mast on which the antenna 1300 is mounted.

[0228] The ground plane 1335 is a conductive surface located at the minimum longitudinal portion of the antenna 1300, as shown in Figure 13B. The ground plane 1335 may extend from the radial symmetry axis 1380 to the maximum radial portion of the dielectric mass 1310. In certain embodiments, the ground plane 1335 may extend beyond the maximum longitudinal portion of the dielectric mass 1310. The ground plane 1335 may be electrically coupled to the second radiator 1315 and to any conductive surface located on the edge 1360B at the minimum longitudinal portion of the dielectric surface 1310.

[0229] The ground plane 1335 can isolate the second radiator 1315 and any cavities located radially inside the second radiator 1315 from the external environment. In certain embodiments, the ground plane 1335 can fix the second radiator 1315. For example, the ground plane 1335 can be fastened, epoxy-bonded, screwed, or bolted to the dielectric mass 1310 to prevent the second radiator 1315 from moving longitudinally or radially. In certain embodiments, the ground plane 1335 can be fixed to the dielectric mass 1310. In certain embodiments, the ground plane 1335 can be fixed to the second radiator 1315. For example, the ground plane 1335 can be fastened to the second radiator 1315, which is a machined copper mass, with one or more conductive screws or bolts.

[0230] In certain embodiments, the ground plane 1335 may be integrated with the second radiator 1315. For example, the ground plane 1335 and the second radiator 1315 may be stamped from a single sheet of conductive material. In certain embodiments, the ground plane 1335 may be part of a larger platform on which the antenna 1300 is mounted. For example, the ground plane 1335 may be the conductive roof of a vehicle.

[0231] The transmission line 1345 can be any suitable transmission line for transmitting and receiving RF energy. The inner conductor or signal conductor of the transmission line 1345 may be electrically coupled to the first radiator 1305. The outer conductor or ground conductor of the transmission line 1345 may be electrically coupled to the second radiator 1315, the ground plane 1335, or both. For example, the outer conductor of a coaxial cable may be soldered to the second radiator 1315 at the feed surface 1350 and also soldered to the ground plane 1335 at the shortest longitudinal portion of the antenna 1300. In another example, the second radiator 1315 and the ground plane 1335 may be formed as a single conductive sheet or conductive block so that the transmission line 1345 is coupled to the ground plane 1335 by coupling the transmission line 1345 to the second radiator 1315. The transmission line 1345 may include a transmission line dielectric that separates the inner conductor or signal conductor from the outer conductor or ground conductor of the transmission line. In certain embodiments, the transmission line dielectric may be fitted to one or more feed surfaces 1350 of the dielectric mass. In certain embodiments, the transmission line 1345 may be azimuthally uniform or radially symmetric. In certain embodiments, the transmission line 1345 may couple the antenna 1300 to the transceiver. In certain embodiments, the transmission line 1345 may extend longitudinally through the ground plane 1335. For example, the transmission line 1345 may extend through the ground plane 1335 to connect to a transceiver that is physically distant from the antenna 1300 or where the ground plane 1335 shields the antenna 1300.

[0232] The pin 1355 may extend longitudinally from the transmission line 1345 to the first radiator 1305 with respect to the radial symmetry axis 1380. In certain embodiments, the radially outer side of the pin 1355 may be mated to one or more feed surfaces 1350. In certain embodiments, the pin 1355 electrically couples the first radiator 1305 to the transmission line 1345. The first radiator 1305 may be soldered, welded, or joined to the pin 1355. As another example, the pin 1355 may be press-fitted into the first radiator 1305. In certain embodiments, the pin 1355 may extend longitudinally within or through the first radiator 1305. For example, pin 1355 may extend longitudinally through the first radiator 1305 and be soldered radially into the first radiator 1305 such that the solder joint is accessible in a cavity on the radially inner side of the first radiator 1305. Coupled the first radiator 1305 to the transmission line 1345 via pin 1355 excites an RF current in the first radiator 1305 over a wide bandwidth.

[0233] The first cavity 1365 occupies a space on the radially inward side of the first radial inner surface 1330, as shown in Figure 13C. In certain embodiments, the first radiator 1305 may be inserted into the first cavity 1365 to present a conductive surface on the first radial inner surface 1330. For example, the first radiator 1305 may be machined from a conductive mass, inserted into the first cavity 1365, and bonded to the first radial inner surface 1330 with epoxy resin.

[0234] In certain embodiments, the first cavity 1365 may be partially or completely filled with dielectric material. For example, the first radiator 1305 may be positioned on the first radial inner surface 1330, and the first cavity 1365 on the radial inner side of the first radiator 1305 may be filled with dielectric material to protect or insulate the radial interior of the first radiator 1305 from the external environment. In certain embodiments, the first radiator 1305 may have the first cavity 1365 partially or completely filled. For example, the first radiator 1305 may be stamped from a thick sheet of conductive material so that the first radiator 1305 partially fills the first cavity 1365. In certain embodiments where the first radiator 1305 is formed without a conductive mass, the first radiator 1305 may not have the first cavity 1365 filled.

[0235] The second cavity 1375 occupies a space on the radially inward side of the second radial inner surface 1340, as shown in Figure 13C. In certain embodiments, the second radiator 1315 may be inserted into the second cavity 1375 to present a conductive surface on the second radial inner surface 1340. In certain embodiments, the second radiator 1315 may also present a conductive surface at the radially widest part of the transmission line 1345. In certain embodiments, the second radiator 1315 may also present a conductive surface on one or more feed surfaces 1350. For example, the second radiator 1315 may be machined from a conductive mass, inserted into the second cavity 1375, and bonded to the second radial inner surface 1340 with epoxy resin.

[0236] In certain embodiments, the second cavity 1375 may be partially or completely filled with dielectric material. For example, the second radiator 1315 may be positioned on the second radial inner surface 1340 and fitted into the transmission line 1345, and the second cavity 1375 on the radial interior side of the second radiator 1315 may be filled with dielectric material to protect or insulate the transmission line 1345 or the radial interior of the second radiator 1315 from the external environment. In certain embodiments, the second radiator 1315 may partially or completely fill the second cavity 1375. For example, the second radiator 1315 may be stamped from a thick sheet of conductive material so that the second radiator 1315 partially fills the second cavity 1375. In certain embodiments where the second radiator 1315 is formed without a conductive mass, the second radiator 1315 may not fill the second cavity 1375. In certain embodiments, the transmission line 1345 may partially fill the second cavity 1375.

[0237] Antenna 1300 may be formed according to any method, operation, steps, parameters, and principles for forming antennas 200, 500, 800, or 1000 that conform to the topology of antenna 1300 shown in Figure 13. Antenna 1300 may be formed according to any method, operation, steps, parameters, and principles that conform to the structure, components, elements, configuration, features, interfaces, or parameters of the first radiator 1305, dielectric mass 1310, second radiator 1315, top hat 1325, and ground plane 1335. Antenna 1300 may be formed from the same or similar materials as the other antennas described herein.

[0238] In certain embodiments, the antenna 1300 may be formed without a conductive mass. For example, so that the antenna 1300 assembled from a first radiator 1305, a second radiator 1315, and a dielectric mass 1310 does not have a conductive mass, the first radiator 1305 may be formed by placing a first conductive surface on a first dielectric base, and the second radiator 1315 may be formed by placing a second conductive surface on a second dielectric base. As another example, so that the antenna 1300 assembled from a first radiator 1305, a second radiator 1315, and a dielectric mass 1310 does not have a conductive mass, the first radiator 1305 may be formed by placing a first conductive surface on a first dielectric base, and the second radiator 1315 may be stamped from a conductive sheet.

[0239] In certain embodiments, the antenna 1300 may be formed from a dielectric unit without a conductive mass. For example, the antenna 1300 may be formed by electrolytic deposition of copper onto a first radial inner surface 1330, a second radial inner surface 1340, and one or more edges 1360A, 1360B to form a dielectric unit. In certain embodiments, one or more surfaces of the dielectric mass 1310 may be masked or treated to control the position of conductive surfaces on the dielectric unit. For example, a non-conductive aperture surface 1320 and one or more feeding surfaces may be partially or completely masked so that the masked surfaces remain non-conductive after the conductive surfaces have been positioned on the dielectric mass 1310.

[0240] In certain embodiments, the antenna 1300 may not have a top hat 1325 or a ground plane 1335. In certain embodiments, the antenna 1300 may be formed by integrating a first radiator 1305 and a top hat 1325, or by integrating a second radiator 1315 and a ground plane 1335. For example, the second radiator 1315 and ground plane 1335 may be machined from a single conductive mass and fitted into a dielectric unit comprising a dielectric mass 1310 and a first radiator 1305 deposited on a first radial inner surface 1330 using electrolytic deposition. As another example, the first radiator 1305 and top hat 1325 may be stamped from a single sheet of conductive material and bonded with epoxy resin to the first radial inner surface 1330 and one or more edges 1360A, 1360B of the dielectric mass 1310.

[0241] In contrast to antennas 200, 500, 800, and 1000, which are not symmetric in the Z dimension, antenna 1300 can be described as having approximately longitudinal symmetry. Antenna 1300 is not perfectly symmetric with respect to the Z dimension due to one or more feeding surfaces 1350 that make the dielectric mass 1310 asymmetric. However, antenna 1300 has some symmetric or approximately symmetric features in the Z dimension, such as the nonconductive aperture surface 1320, the top hat 1325 relative to the ground plane 1335, and the first radiator 1305 relative to the second radiator 1315. The approximately longitudinal symmetry in antenna 1300 may have the advantage of increasing the azimuthal uniformity of the gain and radiation pattern near the horizon (θ=90°).

[0242] Figures 14-15 show the overall radiation pattern and return loss performance of antenna 1300, including the 6:1 bandwidth. 9 This summarizes the wireless performance of the device. 9The performance shown in Figures 14-15 pertains to antenna 1300, which has a ground plane with the same maximum radius as the second radiator 1315. By coupling antenna 1300 to a ground plane with a radius exceeding that of antenna 1300, it is possible to improve the return loss at low frequencies and increase the peak gain while maintaining low distortion performance.

[0243] Figure 14 shows the radiation pattern of antenna 1300 in the elevation plane (ZY or ZX) and the azimuth plane (XY). As shown in the elevation views of Figures 14A and 14B, antenna 1300 maintains a horizontal beam including a radiating horizontal line (θ=90°) over a frequency band of 1–6 fL. In certain embodiments, antenna 1300 can transmit and receive a beam including the horizontal line over a 6:1 pattern bandwidth. Figures 14C and 14D show the radiation pattern of antenna 1300 in the azimuth plane (XY, θ=90°) of 1–6 fL. The azimuth plane pattern of antenna 1300 is substantially uniform in azimuth over a 6:1 pattern bandwidth (1–6 fL), with a maximum variation of ±0.7 dB at 6 fL.

[0244] The return loss of antenna 1300 in Figure 15 exceeds 10 dB over a 6:1 efficiency bandwidth (1–6 fL). Although not shown in Figure 15, the return loss of antenna 1300 exceeds 5 dB over a 6:1 efficiency bandwidth, regardless of the size of the external ground plane on which antenna 1300 is placed. The size of the ground plane has virtually no effect on the return loss performance above 2 fL (i.e., the return loss above 2 fL remains substantially above 10 dB for all ground sizes). Therefore, antenna 1300 is unaffected by placement up to the 10 dB return loss threshold above 2 fL. In certain embodiments, shaping the ground plane to remove surface waves or edge diffraction, or treating the edges or surfaces (e.g., by metasurface or integrated filter), can achieve a return loss of 10 dB in antenna 1300 over a 6:1 bandwidth for any ground plane size.

[0245] As shown in Table 9, the fidelity of radio signals transmitted or received by antenna 1300 exceeds 90% in the frequency band of 1 to 6 fL. In certain embodiments, antenna 1300 can instantaneously transmit and receive radio signals over a single instantaneous bandwidth of up to 6:1. In certain embodiments, antenna 1300 can transmit and receive radio signals over a 6:1 bandwidth, and the 6:1 bandwidth includes a plurality of instantaneous frequency bands, each having a bandwidth that achieves or exceeds the lowest operating frequency.

[0246] [Table 9]

[0247] Antenna 1300 can be configured to obtain desirable radio performance, including a small antenna size, a wide efficiency bandwidth (bandwidth over which the return loss achieves or exceeds the metric, such as 6 dB or 10 dB), a wide instantaneous bandwidth (IBW), and a wide pattern bandwidth (bandwidth over which the radiation pattern achieves or exceeds the metric, such as maintaining a specific gain threshold, conical beam, or horizontal beam), as shown in Table 9 and Figures 14-15. For example, the topology of antenna 1300 determines the position, profile, dimensions, and interaction of the first radiator 1305, the second radiator 1315, and the nonconductive aperture surface 1320 to facilitate maximizing the efficiency bandwidth, IBW, pattern bandwidth, and the overlap between the efficiency bandwidth, IBW, and pattern bandwidth. Similar antenna embodiments disclosed herein also determine the position, profile, dimensions, and interaction of the antenna features to facilitate obtaining wide IBW, efficiency, and pattern performance.

[0248] Figure 16 shows the geometric shape and features of antenna 1600 in perspective and cross-sectional views. The cross-sectional views in Figures 16B and 16C are taken through the center of antenna 1600 shown in Figure 16A. Figure 16B is a cross-sectional view of antenna 1600 with a conductive surface and conductive mass, and Figure 16C is the same cross-sectional view without the conductive surface and conductive mass. Although Figures 16B and 16C show cross-sections in the ZY plane, the same figures can be obtained for cross-sections in any elevation plane (i.e., in any elevation plane θ-r) passing through the center of antenna 1600.

[0249] The dielectric mass 1610 may have multiple surfaces, including a non-conductive aperture surface 1620, a first radial inner surface 1630, a second radial inner surface 1640, one or more feeding surfaces 1650, and one or more edges 1660A, 1660B. The dielectric mass 1610 can be mated to a transmission line 1645. To facilitate reference to various physical features and radio performance characteristics (particularly radiation patterns), Figures 16B and 16C also show an azimuthal plane 1670, a radiation symmetry axis 1680 located at the radiation center of the dielectric mass 1610 (and antenna 1600), and an XYZ coordinate system.

[0250] As shown in Figure 16, the dielectric mass 1610 is azimuthally uniform (without variation according to φ) as can be seen when a cross-section is taken in an arbitrary elevation plane (θ-r plane), yielding the diagrams in Figures 16B and 16C. When the cross-sectional diagrams in Figures 16B and 16C are rotated about the radial symmetry axis 1680, a three-dimensional dielectric mass 1610 is obtained in which each face in the three-dimensional diagram has multiple surfaces corresponding to the curves in the cross-sectional diagrams in Figures 16B and 16C. The dielectric mass 1610 can be radially symmetric or azimuthally uniform with respect to the radial symmetry axis 1680. The dielectric mass 1610 terminates radially inward at a first radial inner surface 1630, a second radial inner surface 1640, and one or more power supply surfaces 1650. The dielectric mass 1610 terminates radially outward at a non-conductive aperture surface 1620. The dielectric block 1610 terminates at its longest longitudinal portion at one or more edges 1660A. Figure 16C shows one edge 1660A at the longest longitudinal portion of the dielectric block 1610. The dielectric block 1610 also terminates at its shortest longitudinal portion at one or more edges 1660B.

[0251] In certain embodiments, the dielectric mass 1610 has a maximum radius determined by the maximum radial (ρ) dimension of the nonconductive opening surface 1620. In certain embodiments, the dielectric mass 1610 has a maximum height determined by the longitudinal (Z) distance between the longest longitudinal portion (edge ​​1660A in Figure 16C) and the shortest longitudinal portion of the dielectric mass 1610 (edge ​​1660B in Figure 16C).

[0252] The dielectric block 1610 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as the dielectric block 1310 in the antenna, conforming to the topology shown in Figure 16. The dielectric block 1610 may be formed according to the same or similar processes, methods, operations, steps, parameters, and principles as the dielectric block 110 or dielectric block 1310. The dielectric block 1610 may be formed from the same or similar material or material composition as the dielectric block 110 or dielectric block 1310.

[0253] The nonconductive aperture surface 1620, located on the radially outer side of the dielectric mass 1610, determines the radial maximum of the dielectric mass 1610. As shown in Figures 16B and 16C, the nonconductive aperture surface 1620 extends longitudinally between two edges 1660A and 1660B. The dielectric mass 1610 terminates at the nonconductive aperture surface 1620 in free space. In certain embodiments, the nonconductive aperture surface 1620 includes a convex surface, a concave surface, or both convex and concave surfaces. Although not shown in Figure 16, in certain embodiments, the radial minimum of the nonconductive aperture surface 1620 may exceed the radial maximum of the first radiator 1605 or the second radiator 1615.

[0254] A first radial inner surface 1630 located on the radially inward side of the dielectric mass 1610 may extend longitudinally from one or more feeding surfaces 1650 to the maximum longitudinal portion of the dielectric mass 1610 (e.g., the edge 1660A in Figure 16C). In certain embodiments without an edge 1660A, the first radial inner surface 1630 may extend radially from one or more feeding surfaces 1650 to the maximum radial portion of the dielectric mass 1610 (e.g., the maximum radial portion of the non-conductive aperture surface 1620 in Figure 16B). In certain embodiments, the first radial inner surface 1630 may include a convex surface, a concave surface, or both convex and concave surfaces. In certain embodiments, a conductive surface may be fitted to the first radial inner surface 1630 during the fabrication of the antenna 1600.

[0255] A second radial inner surface 1640 located on the radially inward side of the dielectric mass 1610 may extend longitudinally from one or more feeding surfaces 1650 to the longitudinal minimum of the dielectric mass 1610. In certain embodiments without an edge 1660B, the second radial inner surface 1640 may extend radially from one or more feeding surfaces 1650 to the radial maximum of the dielectric mass 1610 (for example, the radial maximum of the non-conductive aperture surface 1620 in Figure 16B). In certain embodiments, the second radial inner surface 1640 may include a convex surface, a concave surface, or both convex and concave surfaces. In certain embodiments, a conductive surface may be fitted to the second radial inner surface 1640 during the fabrication of the antenna 1600.

[0256] One or more power supply surfaces 1650 located on the radially inward side of the dielectric mass 1610 may extend radially and longitudinally from the radial minimum of the dielectric mass 1610 to a first radial inner surface 1630, a second radial inner surface 1640, or both. As shown in Figure 16C, one power supply surface extends longitudinally and one power supply surface extends radially. In certain embodiments, the dielectric mass 1610 may have one power supply surface 1650 extending longitudinally between the first radial inner surface 1630 and the second radial inner surface 1640. In certain embodiments, one or more power supply surfaces 1650 may be mated to a transmission line. For example, as shown in Figure 16C, one or more power supply surfaces 1650 may be mated to a coaxial connector or cable, such as a bulkhead, screw-in, or flanged coaxial connector or cable.

[0257] The dielectric mass 1610 may have one or more edges 1660A, 1660B. As shown in Figure 16C, the dielectric mass 1610 includes one edge 1660A at the maximum longitudinal portion of the dielectric mass 1610 and one edge 1660B at the minimum longitudinal portion of the dielectric mass 1610. In certain embodiments, the edges 1660A, 1660B may be included in the dielectric mass 1610 to accommodate manufacturing tolerances or to provide a flat surface (e.g., a flat surface parallel to the XY plane) for mating with other structures, as will be discussed further below. In certain embodiments, the dielectric mass 1610 may not include the edges 1660A, 1660B.

[0258] As shown in Figure 16B, the azimuth plane 1670 defines the radial horizon (θ=90°). In certain embodiments, the azimuth plane 180 may also define an azimuth plane (θ=90°, XY) corresponding to the external ground plane.

[0259] The radial symmetry axis 1680 defines the Z-axis, and with respect to the Z-axis, the dielectric mass 1610 is azimuthally uniform or radially symmetric. An azimuthally uniform structure does not change with respect to the azimuthal angle (φ). The dielectric mass 1610 is azimuthally uniform as shown in Figure 16. In certain embodiments, the dielectric mass 1610 may be radially symmetric to achieve specific RF performance characteristics or to facilitate a specific manufacturing method.

[0260] In certain embodiments, a dielectric unit may be formed from a dielectric mass 1610. To form the dielectric unit, a first conductive surface may be positioned on a first radial inner surface 1630, a second conductive surface may be positioned on a second radial inner surface 1640, or both. Conductive surfaces may also be positioned on one or more power supply surfaces 1650 as needed to provide electrical coupling to a transmission line. In certain embodiments, the first or second conductive surface may also be positioned on one or more edges 1660A, 1660B.

[0261] In certain embodiments, the dielectric mass 1610 (and any corresponding dielectric unit or antenna) may be scaled in one or more radial dimensions. In certain embodiments, scaling may improve directivity in the direction of short radiation axes or planes (axes or planes with smaller scaling factors) or long radiation axes or planes (axes or planes with larger scaling factors). In certain embodiments, the antenna 1600 may be symmetric with respect to the ZX and ZY planes, which include the axis of symmetry.

[0262] Figure 16B shows a cross-sectional view of antenna 1600 comprising a dielectric block 1610. As shown, antenna 1600 may also comprise a first radiator 1605, a second radiator 1615, a top hat 1625, a ground plane 1635, a first cavity 1665, a second cavity 1675, and a dielectric jacket 1690. As shown in Figure 16B, the first radiator 1605, the second radiator 1615, the top hat 1625, and the ground plane 1635 are conductive elements. Antenna 1600 may be electrically coupled to a transmission line 1645 via pin 1655 for transmitting and receiving RF energy. As shown in Figure 16, the maximum radius of antenna 1600 is λ L The maximum height of the antenna 200 is λ, and it does not exceed / 6. LIt does not exceed / 4. Antenna 1600 has a similar topology to antenna 1300, however, in antenna 1600, the dielectric jacket 1690 radially surrounds the pin 1655, the first radiator 1605 presents a conductive surface at the maximum longitudinal portion of the dielectric jacket 1690, and the first radiator 1605 and the second radiator 1615 are symmetrical or nearly symmetrical in the longitudinal direction (i.e., the radial outer surfaces of the first radiator 1605 and the second radiator 1615 present a mirror image structure to RF excitation by the transmission line 1645).

[0263] The first radiator 1605 is located radially inward of the dielectric mass 1610 and presents a conductive surface on the first radial inner surface 1630. The first radiator 1605 may also present a conductive surface on one or more edges 1660A between the first radial inner surface 1630 and the non-conductive aperture surface 1620. The first radiator 1605 may also present a conductive surface on pins extending from a transmission line coupled to the antenna 1600 and on the dielectric jacket. The first radiator 1605 may extend longitudinally from the feeding surface 1650 to the maximum longitudinal portion of the dielectric mass 1610 (e.g., edge 1660A in Figure 16C). In certain embodiments, the first radiator 1605 may extend from an inner conductor of the transmission line (e.g., a pin extending from the transmission line) to the maximum longitudinal portion of the dielectric mass 1610. The first radiator 1605 may be azimuthally uniform or radially symmetric. In certain embodiments, the first radiator 1605 may be symmetric. The first radiator 1605 may extend radially from the inner conductor of the transmission line to one or more edges 1660A of the dielectric mass 1610. In certain embodiments, the first radiator 1605 may extend to the maximum longitudinal radius of the dielectric mass 1610 (for example, to the non-conductive aperture surface 1620 in Figure 16B). In certain embodiments, the first radiator 1605 may include a convex surface, a concave surface, or both convex and concave surfaces.

[0264] In certain embodiments, the space on the radially inner side of the first radiator 1605 is a cavity (e.g., free space or air). In certain embodiments, a dielectric structure (e.g., a dielectric filler) may be inserted into the cavity on the radially inner side of the first radiator 1605.

[0265] The first radiator 1605 may be formed in the same or similar manner, operation, steps, parameters, and principles as the first radiator 1305, corresponding to the antenna 1600 topology shown in Figure 16. In certain embodiments, the first radiator 1605 may be formed or composed of one or more conductive components. For example, the first radiator 1605 may be formed of a conductive sheet or washer (for soldering to the inner conductor of the transmission line) and a deposit of a first conductive surface on the first radial inner surface 1630.

[0266] In certain embodiments, the first radiator 1605 may be fitted into the first radial inner surface 1630 during the construction of the antenna. For example, the first radiator 1605 may be machined from a conductive material and bonded to the first radial inner surface 1630 with epoxy resin. As another example, the first radiator 1605 may be formed by electrolytic emission of a conductor onto a dielectric base, inserted into a cavity on the radially inward side of the first radial inner surface 1630, fitted into the first radial inner surface 1630, and secured by a dielectric mass and a metal top hat or dielectric top hat. The first radiator 1605 may be formed directly on the first radial inner surface 1630. For example, the first radiator 1605 may be formed by spraying a conductive ink or dispersion onto the first radial inner surface 1630.

[0267] In certain embodiments, the first radiator 1605 may be electrically coupled to a transmission line. For example, the first radiator 1605 may be soldered, welded, or joined to a pin extending from the center conductor of the transmission line. As another example, a pin extending from the center conductor of a coaxial connector may be press-fitted into the first radiator 1605.

[0268] In certain embodiments, the first radiator 1605 may be fitted to or electrically coupled to a top hat. For example, the first radiator 1605 may be fixed within the dielectric mass 1610 by a dielectric top hat fastened to the dielectric mass 1610. In another example, the first radiator 1605 may be conductively bonded with epoxy resin to a conductive top hat that prevents current from flowing radially inside the first radiator 1605 in its maximum longitudinal dimension.

[0269] In certain embodiments, the maximum radial dimension of the first radiator 1605 may exceed the minimum radial dimension of the nonconductive aperture surface 1620 (for example, shown in Figure 16B). Reducing the minimum radial dimension of the nonconductive aperture surface 1620 may offer the advantages of thinning the dielectric mass 1610, reducing the weight of the antenna 1600, or increasing the operating bandwidth of the antenna 1600. In certain embodiments, the maximum radial dimension of the nonconductive aperture surface 1620 may exceed the maximum radial dimension of any edge 1660A on the first radiator 1605 and the dielectric mass 1610. Increasing the thickness of the dielectric mass 1610 may have the advantages of lowering the lowest operating frequency of the antenna 1600, improving the return loss of the antenna 1600 near the lowest operating frequency, or controlling the gain or azimuthal uniformity of the radiation pattern at a particular frequency.

[0270] The second radiator 1615 is located radially inward of the dielectric mass 1610 and presents a conductive surface on the second radial inner surface 1640. The second radiator 1615 may also present a conductive surface at one or more edges 1660B between the second radial inner surface 1640 and the non-conductive aperture surface 1620. The second radiator 1615 may extend longitudinally and radially from one or more feeding surfaces 1650 to one or more edges 1660B or the non-conductive aperture surface 1620. In certain embodiments, the second radiator 1615 may extend from the outer conductor of the transmission line (e.g., coaxial cable or connector shield) to the minimum longitudinal portion of the dielectric mass 1610. The second radiator 1615 may be azimuthally uniform or radially symmetric. In certain embodiments, the second radiator 1615 may be symmetric. The second radiator 1615 may extend radially from the outer conductor of the transmission line to one or more edges 1660B of the dielectric mass 1610. In certain embodiments, the second radiator 1615 may extend to the maximum longitudinal radius of the dielectric mass 1610. In certain embodiments, the second radiator 1615 includes a convex surface, a concave surface, or both convex and concave surfaces. In certain embodiments, the second radiator 1615 may have the same maximum radius as the first radiator 1605. In certain embodiments, the second radiator 1615 may have a maximum radius greater than or less than the maximum radius of the first radiator 1605.

[0271] In certain embodiments, the space on the radially inner side of the second radiator 1615 is a cavity (e.g., free space or air). In certain embodiments, a dielectric structure (e.g., a dielectric filler) may be inserted into the cavity on the radially inner side of the second radiator 1615.

[0272] The second radiator 1615 may be formed in the same or similar manner, operation, steps, parameters, and principles as the first radiator 1605, and may be assembled to or integrated with the antenna 1600 in the same or similar manner, operation, steps, parameters, and principles as the first radiator 1605.

[0273] In certain embodiments, the second radiator 1615 may be electrically coupled to a transmission line. For example, the second radiator 1615 may be soldered, welded, or joined to the outer conductor of the transmission line. As another example, the conductive surface of the second radiator 1615 may function as the outer conductor of the transmission line (for example, the conductive surface of the second radiator 1615 may be mated to a dielectric "candlestick" extending from a coaxial connector). Coupled the second radiator 1615 to the transmission line excites an RF current in the second radiator 1615 over a wide bandwidth.

[0274] In certain embodiments, the second radiator 1615 may be mated to or electrically coupled to a ground plane. For example, the second radiator 1615 may be fixed within the dielectric block 1610 by a ground plane fastened to the dielectric block 1610. In another example, the second radiator 1615 may be electrically bonded with epoxy resin to a conductive ground plane that prevents current from flowing radially inside the second radiator 1615 in its minimum longitudinal dimension.

[0275] In certain embodiments, the maximum radial dimension of the second radiator 1615 may exceed the minimum radial dimension of the nonconductive aperture surface 1620 (for example, shown in Figure 16B). In certain embodiments, the maximum radial dimension of the nonconductive aperture surface 1620 may exceed the maximum radial dimension of the second radiator 1615 and any edge 1660B on the dielectric mass 1610.

[0276] As can be seen from a comparison between Figure 13B and Figure 16B, the top hat 1625 in antenna 1600 has substantially the same structure and function as the top hat 1325 in antenna 1300. The top hat 1625 in the antenna may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as the top hat 1325. The top hat 1625 may be formed according to the same or similar methods, operations, steps, parameters, and principles as the top hat 1325.

[0277] As can be seen from a comparison between Figure 13B and Figure 16B, the ground plane 1635 in antenna 1600 has substantially the same structure and function as the ground plane 1335 in antenna 1300. The ground plane 1635 in the antenna may have the same or similar structure, components, elements, configuration, features, interfaces, parameters, or functions as the ground plane 1335. The ground plane 1635 may be formed according to the same or similar methods, operations, steps, parameters, and principles as the ground plane 1335.

[0278] Transmission line 1645 may be any suitable transmission line for transmitting and receiving RF energy. Transmission line 1645 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as transmission line 1345, except that transmission line 1645 interfaces with antenna 1600 as shown in Figure 16B. The dielectric jacket of transmission line 1645 may extend longitudinally beyond the second radiator 1615 and terminate at the first radiator 1605. In certain embodiments, the pins of transmission line 1645 may have the same longitudinal spread as the dielectric jacket, extend longitudinally beyond the second radiator 1615, and terminate at the first radiator 1605.

[0279] Pin 1655 may extend longitudinally from the transmission line 1645 to the first radiator 1605, centered on the radial symmetry axis 1680. In certain embodiments, the radially outer side of pin 1655 may be mated to the dielectric jacket of the transmission line 1645. In certain embodiments, pin 1655 electrically couples the first radiator 1605 to the transmission line 1645. The first radiator 1605 may be soldered, welded, or joined to pin 1655. As another example, pin 1655 may be press-fitted into the first radiator 1605. In certain embodiments, pin 1655 may extend longitudinally beyond the dielectric jacket into or through the first radiator 1605. For example, pin 1655 may extend longitudinally through the first radiator 1605 and be soldered radially into the first radiator 1605 such that the solder joint is accessible in a cavity located radially inside the first radiator 1605.

[0280] The first cavity 1665 occupies a space on the radially inward side of the first radial inner surface 1630, as shown in Figure 16C. In certain embodiments, the first radiator 1605 can be inserted into the first cavity 1665 to present a conductive surface at the maximum longitudinal portion of the first radial inner surface 1630 and the power supply surface 1650. For example, the first radiator 1605 may be machined from a conductive mass, inserted into the first cavity 1665, and bonded to the first radial inner surface 1630 with epoxy resin.

[0281] In certain embodiments, the first cavity 1665 may be partially or completely filled with dielectric material. For example, the first radiator 1605 may be positioned on the first radial inner surface 1630, and the first cavity 1665 on the radial interior side of the first radiator 1605 may be filled with dielectric material to protect or insulate the radial interior of the first radiator 1605 from the external environment. In certain embodiments, the first radiator 1605 may partially or completely fill the first cavity 1665. For example, the first radiator 1605 may be stamped from a thick sheet of conductive material so that the first radiator 1605 partially fills the first cavity 1665. In certain embodiments where the first radiator 1605 is formed without a conductive mass, the first radiator 1605 may not fill the first cavity 1665.

[0282] The second cavity 1675 occupies a space on the radially inward side of the second radial inner surface 1640, as shown in Figure 16C. In certain embodiments, the second radiator 1615 may be inserted into the second cavity 1675 to present a conductive surface on the second radial inner surface 1640. In certain embodiments, the second radiator 1615 may also present a conductive surface at the radially widest part of the transmission line 1645. In certain embodiments, the second radiator 1615 may also present a conductive surface on one or more feed surfaces 1650. For example, the second radiator 1615 may be machined from a conductive mass, inserted into the second cavity 1675, and bonded to the second radial inner surface 1640 with epoxy resin.

[0283] In certain embodiments, the second cavity 1675 may be partially or completely filled with dielectric material. For example, the second radiator 1615 may be positioned on the second radial inner surface 1640 and fitted into the transmission line 1645, and the second cavity 1675 on the radial interior side of the second radiator 1615 may be filled with dielectric material to protect or insulate the transmission line 1645 or the radial interior of the second radiator 1615 from the external environment. In certain embodiments, the second radiator 1615 may partially or completely fill the second cavity 1675. For example, the second radiator 1615 may be stamped from a thick sheet of conductive material so that the second radiator 1615 partially fills the second cavity 1675. In certain embodiments where the second radiator 1615 is formed without a conductive mass, the second radiator 1615 may not fill the second cavity 1675. In certain embodiments, the transmission line 1645 may partially fill the second cavity 1675.

[0284] As shown in Figure 16B, the dielectric jacket 1690 extends longitudinally between the maximum longitudinal portion of the second radial inner surface 1640 and the minimum longitudinal portion of the first radial inner surface 1630. As shown in Figure 16B, the dielectric jacket 1690 fits radially outward of the pin 1655 and extends radially to the minimum radial portion of the dielectric mass 1610. In certain embodiments, the dielectric jacket 1690 may extend beyond the minimum longitudinal portion of the dielectric mass 1610. In certain embodiments, the dielectric jacket 1690 may be a standalone component. For example, the dielectric jacket 1690 may be a ring-shaped or donut-shaped dielectric inserted between the first radiator 1605 and the second radiator 1615 during the assembly of the antenna 1600. In certain embodiments, the dielectric jacket 1690 may be an extension of the dielectric in the transmission line 1645. In certain embodiments, the dielectric jacket may be integrated with the dielectric mass 1610. For example, the dielectric block 1610 may be additively manufactured such that the radial minimum of the dielectric block 1610 extends to the radial maximum of the pin 1655. In certain embodiments, the dielectric jacket 1690 may be omitted from the antenna 1600. Including the dielectric jacket 1690 in the antenna 1600 may have one or more advantages, including fixing the pin 1655, precisely controlling the isolation between the first radiator 1605 and the second radiator 1615, and improving power operation.

[0285] Antenna 1600 may be formed according to any method, operation, steps, parameters, and principles for forming antennas 200, 500, 800, 1000, or 1300 that conform to the topology of antenna 1600 shown in Figure 16. Antenna 1600 may be formed according to any method, operation, steps, parameters, and principles that conform to the structure, components, elements, configuration, features, interfaces, or parameters of the first radiator 1605, dielectric mass 1610, second radiator 1615, top hat 1625, and ground plane 1635. Antenna 1600 may be formed from the same or similar materials as the other antennas disclosed herein.

[0286] In certain embodiments, the antenna 1600 may be formed without a conductive mass. For example, so that the antenna 1600 assembled from a first radiator 1605, a second radiator 1615, and a dielectric mass 1610 does not have a conductive mass, the first radiator 1605 may be formed by placing a first conductive surface on a first dielectric base, and the second radiator 1615 may be formed by placing a second conductive surface on a second dielectric base. As another example, so that the antenna 1600 assembled from a first radiator 1605, a second radiator 1615, and a dielectric mass 1610 does not have a conductive mass, the first radiator 1605 may be stamped from a conductive sheet, and the second radiator 1615 may be formed by placing a first conductive surface on a first dielectric base.

[0287] In certain embodiments, the antenna 1600 may be formed from a dielectric unit without a conductive mass. For example, the antenna 1600 may be formed by electrolytic deposition of copper onto a first radial inner surface 1630, a second radial inner surface 1640, and one or more edges 1660A, 1660B to form a dielectric unit. In certain embodiments, one or more surfaces of the dielectric mass 1610 may be masked or treated to control the position of conductive surfaces on the dielectric unit. For example, a non-conductive aperture surface 1620 and one or more feeding surfaces may be partially or completely masked so that the masked surfaces remain non-conductive after the conductive surfaces have been positioned on the dielectric mass 1610.

[0288] In certain embodiments, the antenna 1600 may not have a top hat 1625 or a ground plane 1635. In certain embodiments, the antenna 1600 may be formed by integrating a first radiator 1605 and a top hat 1625, or by integrating a second radiator 1615 and a ground plane 1635. For example, the second radiator 1615 and ground plane 1635 may be machined from a single conductive mass and fitted into a dielectric unit comprising a dielectric mass 1610 and a first radiator 1605 discharged onto a first radial inner surface 1630. As another example, the first radiator 1605 and top hat 1625 may be stamped from a single sheet of conductive material and bonded with epoxy resin onto the first radial inner surface 1630 and one or more edges 1660A of the dielectric mass 1610.

[0289] In contrast to antennas 200, 500, 800, and 1000, which are not symmetric in the Z dimension, antenna 1600 can be described as having longitudinal symmetry or near-longitudinal symmetry, depending on the characteristics of the dielectric mass 1610. As shown in Figure 16B, antenna 1600 is not perfectly symmetric in the Z dimension due to a radially extending feeding surface 1650 that makes the dielectric mass 1610 asymmetric. However, antenna 1600 has some degree of symmetric or near-symmetric features in the Z dimension, such as the non-conductive aperture surface 1620, the top hat 1625 relative to the ground plane 1635, and the first radiator 1605 relative to the second radiator 1615. In certain embodiments, the dielectric mass 1610 may be longitudinally symmetric (i.e., symmetric with respect to the midpoint of the longitudinal direction). For example, the dielectric mass 1610 may have a single longitudinal feeding surface 1650 such that the first cavity 1665 and the second cavity 1675 are mirror images of each other with respect to the longitudinal midpoint of the dielectric mass 1610. Since the first radiator 1605 and the second radiator 1615 present the same (mirror image) structure with respect to RF excitation by the transmission line 1645, in embodiments where the dielectric mass 1610 is longitudinally symmetric, the antenna 1600 can be described as longitudinally symmetric. Longitudinal symmetry in the antenna 1600 may have the advantage that the gain and azimuthal uniformity of the radiation pattern increase near the horizontal (θ=90°).

[0290] The topology of dielectric block 1610 (and antenna 1600) may have one or more advantages compared to the topology of dielectric block 1310 (and antenna 1300). For example, dielectric block 1310 has a radial feeding surface 1350, which is larger than any radial feeding surface 1650 of dielectric block 1610 and may hinder impedance matching of antenna 1300. If the radial feeding surface 1650 is present, reducing or removing it may facilitate impedance matching of antenna 1600 and improve the symmetry of antenna 1600. The topology of dielectric block 1310 (and antenna 1300) may also have one or more advantages compared to the topology of dielectric block 1610 (and antenna 1600). For example, in antenna 1600, the first radiator 1605 has radial surfaces that fit into the maximum longitudinal portion of the dielectric jacket 1690, which increases the capacitance at the coupling between the transmission line 1645 and antenna 1600 and may require an additional step in forming the first radiator 1605. In contrast, the first radiator 1305 of antenna 1300 is radially tapered up to the maximum radius of pin 1355, reducing capacitance and simplifying the step of forming the first radiator 1305.

[0291] Figures 17-18 show the overall radiation pattern and return loss performance of antenna 1600, including the 6:1 bandwidth. 10 This summarizes the wireless performance of the device. 10 The performance shown in Figures 17-18 relates to antenna 1600, which has a ground plane with the same maximum radius as the second radiator 1615. By coupling antenna 1600 to a ground plane with a radius greater than that of antenna 1600, it is possible to improve the return loss at low frequencies and increase the peak gain while maintaining low distortion performance.

[0292] Figure 17 shows the radiation pattern of antenna 1600 in the elevation plane (ZY or ZX) and the azimuth plane (XY). As shown in the elevation views of Figures 17A and 17B, antenna 1600 maintains a horizontal beam including a radiating horizontal line (θ=90°) over a frequency band of 1–6 fL. In certain embodiments, antenna 1600 can transmit and receive a beam including the horizontal line over a 6:1 pattern bandwidth. Figures 17C and 17D show the radiation pattern of antenna 1600 in the azimuth plane (XY, θ=90°) of 1–6 fL. The azimuth plane pattern of antenna 1600 is substantially uniform in azimuth over a 6:1 pattern bandwidth (1–6 fL), with maximum variation of ±0.6 dB at 1 fL and 2.5 fL.

[0293] The return loss of antenna 1600 in Figure 18 exceeds 10 dB over the 6:1 efficiency bandwidth (1–6 fL). Although not shown in Figure 18, the return loss of antenna 1600 exceeds 6 dB over the 6:1 efficiency bandwidth, regardless of the size of the external ground plane on which antenna 1600 is placed. The size of the ground plane has virtually no effect on the return loss performance above 1.5 fL (i.e., the return loss above 1.5 fL remains substantially above 10 dB for all ground sizes). Therefore, antenna 1600 is unaffected by placement above 1.5 fL, including 1.5–6 fL, for a return loss threshold of 10 dB, and antenna 1600 is unaffected by placement between 1–6 fL, for a return loss threshold of 6 dB. In certain embodiments, shaping the ground plane to eliminate surface waves or edge diffraction, or treating the edges or surfaces (e.g., by a metasurface or integrated filter), can achieve a return loss of 10 dB in antenna 1600 over a 6:1 bandwidth for any ground plane size.

[0294] As shown in Table 10, the fidelity of radio signals transmitted or received by antenna 1600 exceeds 80% in the frequency band of 1 to 6 fL. In certain embodiments, antenna 1600 can instantaneously transmit and receive radio signals over a single instantaneous bandwidth of up to 6:1. In certain embodiments, antenna 1600 can transmit and receive radio signals over a 6:1 bandwidth, and the 6:1 bandwidth includes a plurality of instantaneous frequency bands, each having a bandwidth that achieves or exceeds the lowest operating frequency.

[0295] [Table 10]

[0296] Figures 19A and 19C show the geometric shape and features of antenna 1900 in perspective and cross-sectional views. The cross-sectional views in Figures 19B and 19C are taken through the center of antenna 1900 shown in Figure 19A. Figure 19B is a cross-sectional view of antenna 1900 with a conductive surface and conductive mass, and Figure 19C is the same cross-sectional view without a conductive surface and conductive mass. Figures 19B and 19C show cross-sections in the ZY plane, but the same figures can be obtained in any elevation plane cross-section passing through the center of antenna 1900 (i.e., in any elevation plane θ-r).

[0297] The dielectric mass 1910 may have multiple surfaces, including a non-conductive aperture surface 1920, a first radial inner surface 1930, a second radial inner surface 1940, one or more feeding surfaces 1950, and one or more edges 1960A, 1960B. The dielectric mass 1910 can be mated to a transmission line 1945. To facilitate reference to various physical features and radio performance characteristics (particularly radiation patterns), Figure 19B also shows an azimuthal plane 1970, a radiation symmetry axis 1980 located at the radiation center of the dielectric mass 1910 (and antenna 1900), and an XYZ coordinate system.

[0298] As shown in Figure 19, the dielectric mass 1910 is azimuthally uniform (without variation according to φ), as can be seen in Figures 19B and 19C when a cross-section is taken in an arbitrary elevation plane (θ-r plane). When the cross-sectional views of Figures 19B and 19C are rotated about the radial symmetry axis 1980, a three-dimensional dielectric mass 1910 is obtained in which each face in the three-dimensional view has multiple surfaces corresponding to the curves in the cross-sectional views of Figures 19B and 19C. The dielectric mass 1910 can be radially symmetric or azimuthally uniform with respect to the radial symmetry axis 1980. The dielectric mass 1910 terminates radially inward at a first radial inner surface 1930, a second radial inner surface 1940, and one or more power supply surfaces 1950. The dielectric mass 1910 terminates radially outward at a non-conductive aperture surface 1920. The dielectric block 1910 terminates at its longitudinal maximum portion at one or more edges 1960A. Figure 19C shows one edge 1960A at the longitudinal maximum portion of the dielectric block 1910. The dielectric block 1910 also terminates at its longitudinal minimum portion at one or more edges 1960B.

[0299] In certain embodiments, the dielectric mass 1910 has a maximum radius determined by the maximum radial (ρ) dimension of the nonconductive opening surface 1920. In certain embodiments, the dielectric mass 1910 has a maximum height determined by the longitudinal (Z) distance between the longitudinal maximum portion (e.g., edge 1960A in Figure 19C) and the longitudinal minimum portion of the dielectric mass 1910 (e.g., edge 1960B in Figure 19C).

[0300] Dielectric block 1910 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as dielectric block 1310 or dielectric block 1610 in the antenna, conforming to the topology shown in Figure 19. Dielectric block 1910 may be formed according to the same or similar processes, methods, operations, steps, parameters, and principles as dielectric block 110, dielectric block 1310, or dielectric block 1610. Dielectric block 1910 may be formed from the same or similar material or material composition as dielectric block 110, dielectric block 1310, or dielectric 1610.

[0301] The nonconductive aperture surface 1920, located on the radially outer side of the dielectric mass 1910, determines the radial maximum of the dielectric mass 1910. As shown in Figures 19B and 19C, the nonconductive aperture surface 1920 extends longitudinally between two edges 1960A and 1960B. The dielectric mass 1910 terminates at the nonconductive aperture surface 1920 in free space. In certain embodiments, the nonconductive aperture surface 1920 includes a convex surface, a concave surface, or both convex and concave surfaces. Although not shown in Figure 19B, in certain embodiments, the radial minimum of the nonconductive aperture surface 1920 may exceed the radial maximum of the first radiator 1905 or the second radiator 1915.

[0302] A first radial inner surface 1930 located on the radially inward side of the dielectric mass 1910 may extend longitudinally from one or more feeding surfaces 1950 to the maximum longitudinal portion of the dielectric mass 1910 (e.g., the edge 1960A in Figure 19C). In certain embodiments, the first radial inner surface 1930 may extend radially from the minimum radial portion of the dielectric mass 1910 to the edge 1960A (or, in embodiments without an edge 1960A, to the non-conductive aperture surface 1920). In certain embodiments, the first radial inner surface 1930 may include a convex surface, a concave surface, or both convex and concave surfaces. In certain embodiments, a conductive surface may be fitted to the first radial inner surface 1930 during the fabrication of the antenna 1900.

[0303] A second radial inner surface 1940 located on the radially inward side of the dielectric mass 1910 may extend longitudinally from one or more feeding surfaces 1950 to the longitudinal minimum of the dielectric mass 1910 at one or more edges 1960B. In certain embodiments, the second radial inner surface 1940 may extend radially from one or more feeding surfaces 1950 to the edge 1960B at the longitudinal minimum of the dielectric mass 1910 (or, in embodiments without edges 1960B, to a non-conductive aperture surface 1920). In certain embodiments, the second radial inner surface 1940 may include a convex surface, a concave surface, or both convex and concave surfaces. In certain embodiments, a conductive surface may be fitted to the second radial inner surface 1940 during the fabrication of the antenna 1900.

[0304] One or more feeding surfaces 1950 located on the radially inward side of the dielectric mass 1910 may extend radially from the radial minimum of the dielectric mass 1910 to the radial minimum of the second radial inner surface 1940, and longitudinally from the radial minimum of the first radial inner surface 1930 to the longitudinal maximum of the second radial inner surface 1940. As shown in Figure 19C, one feeding surface extends longitudinally and one feeding surface extends radially. In certain embodiments, one or more feeding surfaces 1950 may be mated to a transmission line. For example, as shown in Figure 19C, one or more feeding surfaces 1950 may be mated to a coaxial connector or cable, such as a bulkhead, screw-in, or flanged coaxial connector or cable.

[0305] The dielectric mass 1910 may have one or more edges 1960A, 1960B. As shown in Figure 19C, the dielectric mass 1910 includes one edge 1960A at the maximum longitudinal portion of the dielectric mass 1910 and one edge 1960B at the minimum longitudinal portion of the dielectric mass 1910. In certain embodiments, the edges 1960A, 1960B may be included in the dielectric mass 1910 to accommodate manufacturing tolerances or to provide a flat surface (e.g., a flat surface parallel to the XY plane) for mating with other structures. In certain embodiments, the dielectric mass 1910 may not include the edges 1960A, 1960B.

[0306] As shown in Figure 19B, the azimuth plane 1970 defines the radial horizon (θ=90°). In certain embodiments, the azimuth plane 180 may also define an azimuth plane (θ=90°, XY) corresponding to the external ground plane.

[0307] The radial symmetry axis 1980 defines the Z-axis, and with respect to the Z-axis, the dielectric mass 1910 is azimuthally uniform or radially symmetric. An azimuthally uniform structure does not change with respect to the azimuthal angle (φ). The dielectric mass 1910 is azimuthally uniform as shown in Figure 19. In certain embodiments, the dielectric mass 1910 may be radially symmetric to achieve specific RF performance characteristics or to facilitate a specific manufacturing method.

[0308] In certain embodiments, a dielectric unit may be formed from a dielectric mass 1910. To form the dielectric unit, a first conductive surface may be positioned on a first radial inner surface 1930, a second conductive surface may be positioned on a second radial inner surface 1940, or both. In certain embodiments, the first or second conductive surface may also be positioned on one or more edges 1960A, 1960B.

[0309] In certain embodiments, the dielectric mass 1910 (and any corresponding dielectric unit or antenna) may be scaled in one or more radial dimensions. In certain embodiments, scaling may improve directivity in the direction of short radiation axes or planes (axes or planes with smaller scaling factors) or long radiation axes or planes (axes or planes with larger scaling factors). In certain embodiments, the antenna 1900 may be symmetric with respect to the ZX and ZY planes, which include the axis of symmetry.

[0310] Figure 19B shows a cross-sectional view of antenna 1900 comprising a dielectric block 1910. As shown, antenna 1900 may also comprise a first radiator 1905, a second radiator 1915, a top hat 1925, a ground plane 1935, a first cavity 1965, a second cavity 1975, and a dielectric jacket 1990. As shown in Figure 19B, the first radiator 1905, the second radiator 1915, the top hat 1925, and the ground plane 1935 are conductive elements. Antenna 1900 may be electrically coupled to a transmission line 1945 via pin 1955 for transmitting and receiving RF energy. As shown in Figure 19, the maximum radius of antenna 1900 is λ L The maximum height of the antenna 200 is λ, and it does not exceed / 6. L It does not exceed / 4. Antenna 1900 has a similar topology to antenna 1600, however, in antenna 1900, the dielectric mass 1910 extends radially inward to pin 1945, and the first radiator 1905 does not present a conductive surface at the maximum longitudinal portion of the dielectric jacket 1940.

[0311] The first radiator 1905 is located radially inward of the dielectric mass 1910 and presents a conductive surface on the first radial inner surface 1930. The first radiator 1905 may also present a conductive surface on one or more edges 1960A between the first radial inner surface 1930 and the non-conductive aperture surface 1920. The first radiator 1905 may also present a conductive surface on a pin extending from the transmission line to the antenna 1900. The first radiator 1905 may extend longitudinally from the feeding surface 1950 to the maximum longitudinal portion of the dielectric mass 1910 (e.g., edge 1960A in Figure 19C). In certain embodiments, the first radiator 1905 may extend from an inner conductor of the transmission line (e.g., a pin extending from the transmission line) to the maximum longitudinal portion of the dielectric mass 1910. The first radiator 1905 may be azimuthally uniform or radially symmetric. In certain embodiments, the first radiator 1905 may be symmetric. The first radiator 1905 may extend radially from the inner conductor of the transmission line to one or more edges 1960A of the dielectric mass 1910. In certain embodiments, the first radiator 1905 may extend to the maximum longitudinal radius of the dielectric mass 1910 (e.g., the nonconductive aperture surface 1920 in Figure 19B). In certain embodiments, the first radiator 1905 may include a convex surface, a concave surface, or both convex and concave surfaces.

[0312] In certain embodiments, the space on the radially inner side of the first radiator 1905 is a cavity (e.g., free space or air). In certain embodiments, a dielectric structure (e.g., a dielectric filler) may be inserted into the cavity on the radially inner side of the first radiator 1905.

[0313] The first radiator 1905 can be formed in accordance with the same or similar methods, operations, steps, parameters, and principles as the first radiator 1305 or the first radiator 1605, in accordance with the antenna 1900 topology shown in Figure 19.

[0314] In certain embodiments, the first radiator 1905 may be fitted into the first radial inner surface 1930 during the construction of the antenna. For example, the first radiator 1905 may be machined from a conductive material and bonded to the first radial inner surface 1930 with epoxy resin. As another example, the first radiator 1905 may be formed by electrolytic emission of a conductor onto a dielectric base, inserted into a cavity on the radially inward side of the first radial inner surface 1930, fitted into the first radial inner surface 1930, and secured by a dielectric mass and a metal top hat or dielectric top hat. The first radiator 1905 may be formed directly on the first radial inner surface 1930. For example, the first radiator 1905 may be formed by spraying a conductive ink or dispersion onto the first radial inner surface 1930.

[0315] In certain embodiments, the first radiator 1905 may be electrically coupled to a transmission line. For example, the first radiator 1905 may be soldered, welded, or joined to a pin extending from the central conductor of the transmission line. As another example, a pin extending from the central conductor of a coaxial connector may be press-fitted into the first radiator 1905.

[0316] In certain embodiments, the first radiator 1905 may be fitted to or electrically coupled to a top hat. For example, the first radiator 1905 may be fixed within the dielectric mass 1910 by a dielectric top hat fastened to the dielectric mass 1910. In another example, the first radiator 1905 may be conductively bonded with epoxy resin to a conductive top hat that prevents current from flowing radially inside the first radiator 1905 in its maximum longitudinal dimension.

[0317] In certain embodiments, the maximum radial dimension of the first radiator 1905 may exceed the minimum radial dimension of the nonconductive aperture surface 1920 (for example, shown in Figure 19B). Reducing the minimum radial dimension of the nonconductive aperture surface 1920 may offer the advantages of thinning the dielectric mass 1910, reducing the weight of the antenna 1900, or increasing the operating bandwidth of the antenna 1900. In certain embodiments, the minimum radial dimension of the nonconductive aperture surface 1920 may exceed the maximum radial dimension of the first radiator 1905. Increasing the thickness of the dielectric mass 1910 may have the advantages of lowering the lowest operating frequency of the antenna 1900, improving the return loss of the antenna 1900 near the lowest operating frequency, or controlling the gain or azimuthal uniformity of the radiation pattern at a particular frequency.

[0318] The second radiator 1915 is located radially inward of the dielectric mass 1910 and presents a conductive surface to the second radial inner surface 1940. The second radiator 1915 may also present a conductive surface at one or more edges 1960B between the second radial inner surface 1940 and the non-conductive aperture surface 1920. The second radiator 1915 may extend longitudinally and radially from one or more feeding surfaces 1950 to one or more edges 1960B or the non-conductive aperture surface 1920. In certain embodiments, the second radiator 1915 may extend from the outer conductor of the transmission line (e.g., coaxial cable or connector shield) to the minimum longitudinal portion of the dielectric mass 1910. The second radiator 1915 may be azimuthally uniform or radially symmetric. In certain embodiments, the second radiator 1915 may be symmetric. The second radiator 1915 may extend radially from the outer conductor of the transmission line to one or more edges 1960B of the dielectric mass 1910. In certain embodiments, the second radiator 1915 may extend to the maximum longitudinal radius of the dielectric mass 1910. In certain embodiments, the second radiator 1915 includes a convex surface, a concave surface, or both convex and concave surfaces. In certain embodiments, the second radiator 1915 may have the same maximum radius as the first radiator 1905. In certain embodiments, the second radiator 1915 may have a maximum radius greater than or less than the maximum radius of the first radiator 1905.

[0319] In certain embodiments, the space on the radially inner side of the second radiator 1915 is a cavity (e.g., free space or air). In certain embodiments, a dielectric structure (e.g., a dielectric filler) may be inserted into the cavity on the radially inner side of the second radiator 1915.

[0320] The second radiator 1915 may be formed in the same or similar manner, operation, steps, parameters, and principles as the first radiator 1905, and may be assembled to or integrated with the antenna 1900 in the same or similar manner, operation, steps, parameters, and principles as the first radiator 1905.

[0321] In certain embodiments, the second radiator 1915 may be electrically coupled to a transmission line. For example, the second radiator 1915 may be soldered, welded, or joined to the outer conductor of the transmission line. As another example, the conductive surface of the second radiator 1915 may function as the outer conductor of the transmission line (for example, the conductive surface of the second radiator 1915 may be mated to a dielectric "candlestick" extending from a coaxial connector). Coupled the second radiator 1915 to the transmission line excites an RF current in the second radiator 1915 over a wide bandwidth.

[0322] In certain embodiments, the second radiator 1915 may be mated to or electrically coupled to a ground plane. For example, the second radiator 1915 may be fixed within the dielectric block 1910 by a ground plane fastened to the dielectric block 1910. In another example, the second radiator 1915 may be conductively bonded with epoxy resin to a conductive ground plane that prevents current from flowing radially inside the second radiator 1915 in its minimum longitudinal dimension.

[0323] In certain embodiments, the maximum radial dimension of the second radiator 1915 may exceed the minimum radial dimension of the nonconductive aperture surface 1920 (for example, shown in Figure 19B). In certain embodiments, the maximum radial dimension of the nonconductive aperture surface 1920 may exceed the maximum radial dimension of the second radiator 1915 and any edge 1960B on the dielectric mass 1910.

[0324] As can be seen from a comparison of Figures 13B, 16B, and 19B, the top hat 1925 in antenna 1900 has substantially the same structure and function as the top hat 1325 in antenna 1300 and the top hat 1625 in antenna 1600. The top hat 1925 in the antenna may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as the top hat 1325 or the top hat 1625. The top hat 1925 may be formed according to the same or similar methods, operations, steps, parameters, and principles as the top hat 1325 or the top hat 1625, or from the same or similar materials.

[0325] As can be seen from a comparison of Figures 13B, 16B, and 19B, the ground plane 1935 in antenna 1900 has substantially the same structure and function as the ground plane 1335 in antenna 1300 and the ground plane 1635 in antenna 1600. The ground plane 1935 in the antenna may have the same or similar structure, components, elements, configuration, features, interfaces, parameters, or functions as the ground plane 1335 or the ground plane 1635. The ground plane 1935 may be formed according to the same or similar methods, operations, steps, parameters, and principles as the ground plane 1335 or the ground plane 1635.

[0326] Transmission line 1945 may be any suitable transmission line for transmitting and receiving RF energy. Transmission line 1945 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as transmission line 1345 or transmission line 1645, except that transmission line 1945 interfaces with antenna 1900 as shown in Figure 19B. The dielectric jacket of transmission line 1945 may extend longitudinally beyond the second radiator 1915 and terminate at the first radiator 1905. In certain embodiments, the pins of transmission line 1945 may have the same longitudinal spread as the dielectric jacket, extend longitudinally beyond the second radiator 1915, and terminate at the first radiator 1905.

[0327] Pin 1955 may extend longitudinally from the transmission line 1945 to the first radiator 1905, centered on the radial symmetry axis 1980. In certain embodiments, the radially outer end of pin 1955 may mate into the dielectric jacket of the transmission line 1945. In certain embodiments, pin 1955 electrically couples the first radiator 1905 to the transmission line 1945. The first radiator 1905 may be soldered, welded, or joined to pin 1955. As another example, pin 1955 may be press-fitted into the first radiator 1905. In certain embodiments, pin 1955 may extend longitudinally beyond the dielectric jacket into or through the first radiator 1905. For example, pin 1955 may be soldered radially into the first radiator 1905 such that it extends longitudinally through the first radiator 1905 and the solder joint is accessible in a cavity located radially inside the first radiator 1905.

[0328] The first cavity 1965 occupies a space on the radially inward side of the first radial inner surface 1930, as shown in Figure 19C. In certain embodiments, the first radiator 1905 may be inserted into the first cavity 1965 to present a conductive surface on the first radial inner surface 1930 and the pin 1955. For example, the first radiator 1905 may be machined from a conductive mass, inserted into the first cavity 1965, bonded to the first radial inner surface 1930 with epoxy resin, and soldered to the pin 1955.

[0329] In certain embodiments, the first cavity 1965 may be partially or completely filled with dielectric material. For example, the first radiator 1905 may be positioned on the first radial inner surface 1930, and the first cavity 1965 on the radial inner side of the first radiator 1905 may be filled with dielectric material to protect or insulate the radial interior of the first radiator 1905 from the external environment. In certain embodiments, the first radiator 1905 may partially or completely fill the first cavity 1965. For example, the first radiator 1905 may be stamped from a thick sheet of conductive material so that the first radiator 1905 partially fills the first cavity 1965. In certain embodiments where the first radiator 1905 is formed without a conductive mass, the first radiator 1905 may not fill the first cavity 1965.

[0330] The second cavity 1975 occupies a space on the radially inward side of the second radial inner surface 1940, as shown in Figure 19C. In certain embodiments, the second radiator 1915 may be inserted into the second cavity 1975 to present a conductive surface on the second radial inner surface 1940. In certain embodiments, the second radiator 1915 may also present a conductive surface at the radially widest portion of the transmission line 1945. In certain embodiments, the second radiator 1915 may also present a conductive surface on one or more feed surfaces 1950. For example, the second radiator 1915 may be machined from a conductive mass, inserted into the second cavity 1975, and bonded to the second radial inner surface 1940 with epoxy resin.

[0331] In certain embodiments, the second cavity 1975 may be partially or completely filled with dielectric material. For example, the second radiator 1915 may be positioned on the second radial inner surface 1940 and fitted into the transmission line 1945, and the second cavity 1975 on the radial interior side of the second radiator 1915 may be filled with dielectric material to protect or insulate the transmission line 1945 or the radial interior of the second radiator 1915 from the external environment. In certain embodiments, the second radiator 1915 may partially or completely fill the second cavity 1975. For example, the second radiator 1915 may be stamped from a thick sheet of conductive material so that the second radiator 1915 partially fills the second cavity 1975. In certain embodiments where the second radiator 1915 is formed without a conductive mass, the second radiator 1915 may not fill the second cavity 1975. In certain embodiments, the transmission line 1945 may partially fill the second cavity 1975.

[0332] As shown in Figure 19B, the dielectric jacket 1990 extends longitudinally between the maximum longitudinal portion of the second radial inner surface 1940 and the minimum longitudinal portion of the first radial inner surface 1930. As shown in Figure 19B, the dielectric jacket 1990 fits radially to the radially outside of the pin 1955 and extends radially to the minimum radial portion of the second radial inner surface 1940. In certain embodiments, the dielectric jacket 1990 may be a standalone component. For example, the dielectric jacket 1990 may be a ring-shaped or donut-shaped dielectric inserted between the first radiator 1905 and the second radiator 1915 during the assembly of the antenna 1900. In certain embodiments, the dielectric jacket 1990 may be an extension of the dielectric in the transmission line 1945. In certain embodiments, the dielectric jacket may be integrated with the dielectric block 1910. For example, the dielectric block 1910 may be additively manufactured such that the radial minimum of the dielectric block 1910 extends to the radial maximum of the pin 1955. In certain embodiments, the dielectric jacket 1990 may be omitted from the antenna 1900. Including the dielectric jacket 1990 in the antenna 1900 may have one or more advantages, including fixing the pin 1955, precisely controlling the isolation between the first radiator 1905 and the second radiator 1915, mating the transmission line 1945 to the dielectric block 1910 with high reliability, and improving power operation.

[0333] Antenna 1900 may be formed according to any method, operation, steps, parameters, and principles for forming antennas 200, 500, 800, 1000, 1300, or 1600 that conform to the topology of antenna 1900 shown in Figure 19. Antenna 1900 may be formed according to any method, operation, steps, parameters, and principles that conform to the structure, components, elements, configuration, features, interfaces, or parameters of the first radiator 1905, dielectric mass 1910, second radiator 1915, top hat 1925, and ground plane 1935. Antenna 1900 may be formed from the same or similar materials as the other antennas disclosed herein.

[0334] In certain embodiments, the antenna 1900 may be formed without a conductive mass. For example, so that the antenna 1900 assembled from a first radiator 1905, a second radiator 1915, and a dielectric mass 1910 does not have a conductive mass, the first radiator 1905 may be formed by placing a first conductive surface on a first dielectric base, and the second radiator 1915 may be formed by placing a second conductive surface on a second dielectric base. As another example, so that the antenna 1900 assembled from a first radiator 1905, a second radiator 1915, and a dielectric mass 1910 does not have a conductive mass, the first radiator 1905 may be stamped from a conductive sheet, and the second radiator 1915 may be formed by placing a first conductive surface on a first dielectric base.

[0335] In certain embodiments, the antenna 1900 may be formed from a dielectric unit without a conductive mass. For example, the antenna 1900 may form a dielectric unit by electrolytic deposition of copper onto a first radial inner surface 1930, a second radial inner surface 1940, and one or more edges 1960A, 1960B. In certain embodiments, one or more surfaces of the dielectric mass 1910 may be masked or treated to control the position of conductive surfaces on the dielectric unit. For example, a non-conductive aperture surface 1920 and one or more feeding surfaces may be partially or completely masked so that the masked surfaces remain non-conductive after the conductive surfaces have been positioned on the dielectric mass 1910.

[0336] In certain embodiments, the antenna 1900 may not have a top hat 1925 or a ground plane 1935. In certain embodiments, the antenna 1900 may be formed by integrating a first radiator 1905 and a top hat 1925, or by integrating a second radiator 1915 and a ground plane 1935. For example, the second radiator 1915 and ground plane 1935 may be machined from a single conductive mass and fitted into a dielectric unit comprising a dielectric mass 1910 and a first radiator 1905 discharged onto a first radial inner surface 1930. As another example, the first radiator 1905 and top hat 1925 may be stamped from a single sheet of conductive material and bonded with epoxy resin onto the first radial inner surface 1930 and one or more edges 1960A of the dielectric mass 1910.

[0337] In contrast to antennas 200, 500, 800, and 1000, which are not symmetric in the Z dimension, antenna 1900 can be described as having approximately longitudinal symmetry. As shown in Figure 19B, antenna 1900 is not perfectly symmetric in the Z dimension due to one or more feeding surfaces 1950 that make the dielectric mass 1910 asymmetric. However, antenna 1900 has some symmetric or approximately symmetric features in the Z dimension, such as the nonconductive aperture surface 1920, the top hat 1925 relative to the ground plane 1935, and the first radiator 1905 relative to the second radiator 1915. The approximately longitudinal symmetry in antenna 1900 may have the advantage of increasing azimuthal uniformity of gain and radiation pattern near the horizon (θ=90°).

[0338] The topology of dielectric block 1910 (and antenna 1900) may have one or more advantages compared to the topologies of dielectric block 1310 (and antenna 1300) and dielectric block 1610 (and antenna 1600). For example, antenna 1900 has fewer conductive surfaces (compared to antennas 1300 and 1900) near the feed transition where transmission line 1945 couples with antenna 1900. The topologies of dielectric block 1310 (and antenna 1300) and dielectric block 1610 (and antenna 1600) may have one or more advantages compared to the topology of dielectric block 1910 (and antenna 1900). For example, dielectric block 1910 has a smaller minimum feature size (compared to antennas 1300 and 1600).

[0339] Figures 20-21 show the overall radiation pattern and return loss of antenna 1900 across a 6:1 bandwidth. 11 This summarizes the wireless performance of the device. 11 The performance shown in Figures 20-21 relates to antenna 1900, which has a ground plane with the same maximum radius as the second radiator 1915. By coupling antenna 1900 to a ground plane with a radius exceeding that of antenna 1900, it is possible to improve the return loss at low frequencies and increase the peak gain while maintaining low distortion performance.

[0340] Figure 20 shows the radiation pattern of antenna 1900 in the elevation plane (ZY or ZX) and the azimuth plane (XY). As shown in the elevation views of Figures 20A and 20B, antenna 1900 maintains a horizontal beam including a radiating horizontal line (θ=90°) over a frequency band of 1–6 fL. In certain embodiments, antenna 1900 can transmit and receive beams including the horizontal line over a 6:1 pattern bandwidth. Figures 20C and 20D show the radiation pattern of antenna 1900 in the azimuth plane (XY, θ=90°) of 1–6 fL. The azimuth plane pattern of antenna 1900 is substantially uniform in azimuth over a 6:1 pattern bandwidth (1–6 fL), with a maximum variation of ±1 dB at 6 fL.

[0341] The return loss of antenna 1900 in Figure 21 exceeds 10 dB over a 6:1 efficiency bandwidth (1–6 fL). Although not shown in Figure 21, the return loss of antenna 1900 exceeds 6 dB over a 6:1 efficiency bandwidth, regardless of the size of the external ground plane on which antenna 1900 is placed. The size of the ground plane has virtually no effect on the return loss performance above 2 fL (i.e., the return loss above 2 fL remains above 10 dB for all ground sizes). Therefore, antenna 1900 is unaffected by placement above 2 fL, including 2–6 fL. In certain embodiments, shaping the ground plane to remove surface waves or edge diffraction, or treating the edges or surfaces (e.g., by metasurface or integrated filter), can achieve a return loss of 10 dB in antenna 1900 over a 6:1 bandwidth for any ground plane size.

[0342] As shown in Table 11, the fidelity of the radio signal transmitted or received by antenna 1600 exceeds 80% in the frequency band of 1 to 6 fL. In certain embodiments, antenna 1900 can instantaneously transmit and receive radio signals over a single instantaneous bandwidth of up to 6:1. In certain embodiments, antenna 1900 can transmit and receive radio signals over a 6:1 bandwidth, and the 6:1 bandwidth includes a plurality of instantaneous frequency bands, each having a bandwidth that achieves or exceeds the lowest operating frequency.

[0343] [Table 11]

[0344] Figure 22 shows an exemplary spectrum assignment for one or more radio signals transmitted and received by the antenna disclosed herein. As shown in Figure 22, the spectrum assignment is center frequency f cIt may have a protection frequency band that separates the transmit bandwidth and the receive bandwidth. The receive bandwidth, which extends up to 3.2 GHz, may include one or more subbands (e.g., subbands 1-4). The transmit bandwidth, which extends up to 3.2 GHz, may include one or more subbands (e.g., subbands 5-8).

[0345] In certain embodiments, antennas (e.g., antenna 200, antenna 500, antenna 800, antenna 1000, antenna 1300, antenna 1600, antenna 1900, antenna 2400 in Figure 24, or antenna 2700 as a whole in Figure 27) may be configured to transmit and receive radio signals over a plurality of IBWs, each including up to 3.2 GHz. Alternatively or additionally, antennas may be configured to transmit and receive radio signals over IBWs up to 6.4 GHz. In certain embodiments, antennas may be configured to transmit and receive radio signals over a plurality of IBWs, each including at least 3.2 GHz.

[0346] In certain embodiments, an antenna may be coupled to a transmit channel and a receive channel. The antenna may transmit radio signals received from the transmit channel into free space. The antenna may transmit radio signals received from free space to the receive channel. As shown in Figure 22, in certain embodiments, the transmit channel may be configured to instantaneously transmit communications in a transmit frequency band having an IBW of up to 3.2 GHz. In certain embodiments, the transmit channel may be configured to instantaneously transmit communications in a transmit frequency band having an IBW of at least 3.2 GHz. As shown in Figure 22, the receive channel may be configured to instantaneously receive communications in a receive frequency band having an IBW of up to 3.2 GHz. In certain embodiments, the receive channel may be configured to instantaneously receive a second communication in a receive frequency band having an IBW of at least 3.2 GHz. As shown in Figure 22, the transmit frequency band and the receive frequency band may not overlap in frequency.

[0347] Figure 23 shows an exemplary transceiver system that may be used with the antenna embodiments disclosed herein. Those skilled in the art will understand, without loss of generality, that the filtering, amplification, frequency conversion, and switching stages may be added or omitted.

[0348] The transceiver system 2300 may comprise an IF transceiver 2380 and an analog / RF transceiver 2390. The transceiver system 2300 may be connected to one or more antennas 2370. The IF transceiver 2380 may generate, transmit, and receive IF (intermediate frequency, or baseband) signals with the analog / RF transceiver 2390. The IF transceiver 2380 may comprise a digital transceiver 2305, a DAC 2310 (digital-to-analog converter), an ADC 2315 (analog-to-digital converter), a transmit IF filter 2320, and a receive IF filter 2325. The analog / RF transceiver 2390 may transmit and receive analog / RF signals with the IF transceiver 2380 and the antenna 2370. The analog / RF transceiver may comprise an LO2330 (local oscillator), a downconverter 2335, an upconverter 2340, an LNA2345 (low-noise amplifier), an HPA2350 (high-power amplifier), and a TX / RX isolation 2360. The transceiver system 2300 may comprise a transmit channel from the digital transceiver 2305 through the DAC2310, transmit IF filter 2320, upconverter 2340, and HPA2350 to the antenna 2370. The transceiver system 2300 may comprise a receive channel from the antenna 2370 through the LNA2345, downconverter 2335, receive IF filter 2325, and ADC2315 to the digital transceiver 2305. In certain embodiments, circuits, devices, or functions, such as those shown in Figure 23, may be added to or omitted from the transmit or receive channels. In certain embodiments, the transceiver 2300 may comprise only the transmitting circuit and transmitting function required for the transmitting channel, or only the receiving circuit and receiving function required for the receiving channel.

[0349] The digital transceiver 2305 may be any suitable digital system for generating, transmitting, and receiving digital IF signals or baseband signals. In certain embodiments, the digital transceiver 2305 may be implemented as a microprocessor, a field-programmable gate array (FPGA), or an application-specific integrated circuit (ASIC). In certain embodiments, the digital transceiver 2305 may generate, transmit, or receive White Gauss signals. In certain embodiments, the digital transceiver 2305 may generate, transmit, or receive spread spectrum signals. In certain embodiments, the digital transceiver 2305 may generate, transmit, or receive uncharacterized signals. In certain embodiments for direct digital conversion, the digital transceiver 2305 may generate, transmit, or receive RF signals without up-converting or down-converting in the analog / RF transceiver 2390.

[0350] DAC2310 can be any suitable digital-to-analog converter for converting digital signals to analog or RF signals. DAC2310 can convert digital signals to analog or RF signals over multiple channels (e.g., subbands 5-8 in Figure 22). In certain embodiments, DAC2310 may include multiplexing multiple channels into a single channel. In certain embodiments, DAC2310 may include a discrete DAC. In certain embodiments, DAC2310 may be integrated with a digital transceiver 2305. For example, DAC2310 may comprise a digital-to-analog converter implemented on an FPGA. In certain embodiments, DAC2310 may be configured to convert digital signals to analog or RF signals over a wide bandwidth (e.g., 6:1, 8:1, or 10:1 bandwidth as disclosed herein) with high fidelity.

[0351] The ADC2315 can be any suitable analog-to-digital converter for converting analog or RF signals to digital signals. The ADC2315 can convert digital signals to analog or RF signals over multiple channels (e.g., subbands 1-4 in Figure 22). In certain embodiments, the ADC2315 may include multiplexing multiple channels into a single channel. In certain embodiments, the ADC2315 may be integrated with a digital transceiver 2305. For example, the ADC2315 may include an analog-to-digital converter implemented on an FPGA. In certain embodiments, the ADC2315 may be configured to convert analog or RF signals to digital signals with high fidelity over a wide bandwidth (e.g., a 6:1, 8:1, or 10:1 bandwidth as disclosed herein).

[0352] The transmit IF filter 2320 may be any suitable filter for filtering and adjusting the IF signal or passband signal for upconversion to RF. The receive IF filter 2325 may be any suitable filter for filtering and adjusting the IF signal or passband signal downconverted from RF.

[0353] The LO2330 can be any local oscillator suitable for generating a stable carrier signal. The LO2330 may include a crystal oscillator, a variable frequency oscillator, a temperature-controlled oscillator, a frequency synthesizer, or a similar device for obtaining a stable carrier.

[0354] The downconverter 2335 can be any suitable circuit for downconverting an RF signal to an IF signal or a baseband signal. For example, the downconverter 2335 may include a mixer that downconverts from the RF frequency band to IF or baseband by mixing with the carrier (LO) frequency. In certain embodiments, the downconverter 2335 may include a filtering circuit or a matching circuit.

[0355] The upconverter 2340 can be any suitable circuit for upconverting an IF signal or passband signal to an RF signal. For example, the upconverter 2340 may include a mixer that upconverts from the IF or baseband frequency band to the RF band by mixing with the carrier (LO) frequency. In certain embodiments, the upconverter 2340 may include a filtering circuit or a matching circuit.

[0356] In certain embodiments, the downconverter 2335 or upconverter 2340 may include one or more frequency multipliers or frequency dividers. For example, the upconverter 2340 may upconvert the IF signal to an RF signal by passing the harmonics of the IF signal through.

[0357] The LNA2345 can be any suitable low-noise amplifier for amplifying low-power signals without degrading the signal-to-noise (SNR) ratio. In certain embodiments, the LNA2345 may be configured to amplify broadband radio signals in any frequency band or bandwidth disclosed herein (e.g., signals up to 6.4 GHz or signals spanning a 6:1 bandwidth). For example, the LNA2345 may be configured to amplify received signals from 1 to 6 GHz with low noise figure, low distortion, gain flatness, high IP3, and a wide dynamic range over a wide temperature range. In certain embodiments, the LNA2345 may be cascaded amplifiers or distributed throughout the entire receiving chain. In certain embodiments, the LNA2345 may include filtering or matching circuits.

[0358] The HPA2350 can be any suitable high-power amplifier for amplifying high-power RF signals. In certain embodiments, the HPA2350 may be configured to amplify broadband radio signals in any frequency band or bandwidth disclosed herein (e.g., signals up to 6.4 GHz or signals spanning a 6:1 bandwidth). For example, the HPA2350 may be configured to amplify 1–6 GHz transmit signals with high power, gain flatness, wide dynamic range, and high linearity over a wide temperature range. In certain embodiments, the HPA2350 may be a cascade of amplifiers or distributed throughout the entire transmit chain. In certain embodiments, the HPA2350 may include filtering or matching circuits.

[0359] The TX / RX isolation 2360 can be any suitable circuit or device for separating the transmit (TX) channel from the receive (RX) channel. The TX / RX isolation 2360 may include one or more filters, power dividers, duplexers, diplexers, circulators, limiters, or RF switches. In certain embodiments, a combination of the TX / RX isolation 2360 and spectrum assignment can separate the transmit channel from the receive channel. For example, a diplexer implemented in the TX / RX isolation 2360 can separate the transmit signal in the transmit band from the receive signal in the receive band, which has a lower frequency than the transmit band. In certain embodiments, a combination of the TX / RX isolation 2360 and signal spreading can separate the transmit channel from the receive channel. For example, a circulator implemented in the TX / RX isolation 2360 may provide 20 dB of isolation between the transmit channel and the receive channel, and signal spreading may provide up to 50 dB of transmit signal rejection on the receive channel.

[0360] Antenna 2370 may be any antenna configured for instantaneous transmission and reception of broadband radio signals, as disclosed herein. Antenna 2370 may be one or more of Antenna 200, Antenna 500, Antenna 800, Antenna 1000, Antenna 1300, Antenna 1600, Antenna 1900, Antenna 2400, Antenna 2700, or any combination thereof. In certain embodiments, Antenna 2370 may be an array of antenna elements. In certain embodiments, multiple transceiver systems 2300 may be connected to multiple antennas 2370 to form a multi-channel antenna array.

[0361] In certain embodiments, the DAC2310 and ADC2315 can synthesize an IF signal or a baseband signal, each having an IBW of up to 3.2 GHz. As shown in Figure 23, for transmission or reception via antenna 2370, the transmit chain upconverts the IF signal to the RF bandwidth, and the receive chain downconverts the IF signal from the RF bandwidth. In certain embodiments, the transmit IF filter 2320 and the receive IF filter 2325 (lowpass or bandpass, respectively) can filter and adjust the IF signal before upconversion or after downconversion. In certain embodiments, a transmit signal of up to 3.2 GHz can be transmitted over the radio channel via antenna 2370 without upconversion (e.g., by removing the upconverter 2340 in Figure 23). In certain embodiments, a receive signal of up to 3.2 GHz can be received over the radio channel via the antenna without downconversion (e.g., by removing the downconverter 2335 in Figure 23).

[0362] In certain embodiments, LO2330 may provide spreading codes for mixing into the transmit or receive communication during upconversion or downconversion, respectively. In certain embodiments, the transmit channel and the receive channel may have separate LOs such that the transmit spreading code and the receive spreading code are different codes. In certain embodiments, the transmit channel and the receive channel may share a single LO2330, and the digital transceiver 2305 may spread the transmit signal or the receive signal. In certain embodiments, only one of the transmit or receive channels may transmit or receive a signal containing a spreading code.

[0363] In certain embodiments, the transmit frequency band and the receive frequency band may not overlap in frequency. In certain embodiments, the transmit channel and the receive channel may be separated based on the transmit band not overlapping with the receive band. This may provide one or more advantages, such as omitting or reducing circuitry (e.g., duplexers, diplexers, circulators, or switches) in the TX / RX isolation 2360 as shown in Figure 23, increasing transmit power, or increasing receive sensitivity and interference rejection. In certain embodiments, the transmit frequency band may be higher in frequency than the receive frequency band. The receive channel may be configured for direct digital down-conversion of the received communication. The transmit channel may be configured for RF up-conversion of the transmitted communication. In certain embodiments, the receive frequency band may be higher in frequency than the transmit frequency band. The transmit channel may be configured for direct digital up-conversion of the transmitted communication. The receive channel may be configured for RF down-conversion of the received communication.

[0364] In certain embodiments, the transmit and receive channels may be configured for half-duplex communication. This may be advantageous as it allows two radio stations (e.g., two radios communicating on a radio channel) to be configured to both directly digital down-convert (receive) or both directly digital up-convert (transmit), simplifies the transceiver architecture, and limits local oscillator leakage (LO).

[0365] In certain embodiments, the transmit channel and the receive channel may be configured for spread spectrum communication. The transmitted communication may include a first spreading code. The received communication may include a second spreading code. In certain embodiments, the transmit channel and the receive channel may be separated on the basis that the first spreading code and the second spreading code are different codes. In certain embodiments, the first spreading code and the second spreading code may be uncorrelated during acquisition and synchronization. In certain embodiments, the transmit band and the receive band may transmit and receive in the same band, or they may transmit and receive in overlapping bands based on the separation of the transmit channel and the receive channel by spread spectrum.

[0366] Figures 24 and 25 as a whole illustrate various structures, components, elements, configurations, features, interfaces, methods, operations, and parameters of a top-hat antenna. The top-hat embodiments discussed with respect to Figures 24 and 25A-25C can also be implemented in other antenna embodiments disclosed herein with little effect on the size or performance of the antenna.

[0367] Figure 24 shows a cross-sectional view of the geometric shape and features of antenna 2400. The cross-sectional view in Figure 24 is taken through the center of antenna 2400. Figure 24 is a cross-sectional view of antenna 2400, comprising the conductive surface and conductive mass of antenna 2400. Although Figure 24 shows a cross-section in the ZY plane, the same figure can be obtained for a cross-section in any elevation plane (i.e., in any elevation plane θ-r) passing through the center of antenna 2400. As shown in Figure 24, antenna 2400 comprises a dielectric mass 2410, a non-conductive aperture surface 2420, a top hat 2430, a dielectric jacket 2440, a dielectric pocket 2450, a first radiator 2405, a second radiator 2415, a ground plane 2425, a transmission line 2435, and a pin 2445. Although not shown in Figure 24, the radial symmetry axis (Z-axis) passes through the center of antenna 2400, and the azimuthal plane (XY plane) coincides with the maximum longitudinal portion of ground plane 2425. As shown in Figure 24, the maximum radius of antenna 2400 is λ L The maximum height of the antenna 2400 is λ, and it does not exceed / 10. L Do not exceed / 6.

[0368] As shown in Figure 24, the dielectric mass 2410 may have multiple surfaces, including a non-conductive aperture surface 2420, a first radial inner surface for fitting into the first radiator, a second radial inner surface for fitting into the second radiator, and one or more edges at the maximum and minimum longitudinal portions of the dielectric mass 2410. The dielectric mass 2410 (and antenna 2400) is azimuthally uniform (without variation according to φ), as shown in Figure 24 when a cross-section is taken in an arbitrary elevation plane (θ-r plane). Rotating the cross-sectional view of Figure 24 around the radial symmetry axis yields a three-dimensional dielectric mass 2410 in which each face in the three-dimensional view corresponds to a curve in the cross-sectional view of Figure 24, with multiple surfaces. The dielectric mass 2410 may be radially symmetric or azimuthally uniform with respect to the radial symmetry axis. The dielectric mass 2410 terminates radially inward at a first radial inner surface, a second radial inner surface, and one or more dielectric pockets 2450. The dielectric mass 2410 terminates radially outward at the nonconductive opening surface 2420. The dielectric mass 2410 terminates at its longitudinal maximum at one or more edges. The dielectric mass 2410 also terminates at its longitudinal minimum at one or more edges.

[0369] Dielectric block 2410 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as dielectric block 1310, dielectric block 1610, or dielectric block 1910 in the antenna, conforming to the topology shown in Figure 24. Dielectric block 2410 may be formed according to the same or similar processes, methods, operations, steps, parameters, and principles as dielectric block 110, dielectric block 1310, dielectric block 1610, or dielectric block 1910. Dielectric block 2410 may be formed from the same or similar material or material composition as dielectric block 110, dielectric block 1310, dielectric 1610, or dielectric block 1910.

[0370] The nonconductive aperture surface 2420, located on the radially outer side of the dielectric mass 2410, determines the radial maximum of the dielectric mass 2410. As shown in Figure 24, the nonconductive aperture surface 2420 extends longitudinally between the two edges of the dielectric mass 2410. The dielectric mass 2410 terminates at the nonconductive aperture surface 2420 in free space. In certain embodiments, the nonconductive aperture surface 2420 includes a convex surface, a concave surface, or both convex and concave surfaces. Although not shown in Figure 24, in certain embodiments, the radial minimum of the nonconductive aperture surface 2420 may exceed the radial maximum of the first radiator, the second radiator, or both. In certain embodiments, the longitudinal maximum of the nonconductive aperture surface 2420 may correspond to the longitudinal minimum of the top hat.

[0371] The top hat 2430 is located on the longitudinally maximum side of the dielectric block 2410, as shown in Figure 24. In certain embodiments, the top hat 2430 extends from the radial symmetry axis at the center of the antenna 2400 to the maximum radius of the dielectric block 2410. In certain embodiments, the top hat 2430 may extend radially beyond the maximum radius of the dielectric block 2410. In certain embodiments, the maximum radius of the dielectric block 2410 may exceed the maximum radius of the top hat 2430. The top hat 2430 may be thin enough that it does not affect the height of the antenna 2400. For example, the height of the antenna 2400 is λ with or without the top hat 2430. L It can be anything less than / 6.

[0372] The top hat 2430 may be formed from the same or similar materials or material compositions as any dielectric mass disclosed herein. In certain embodiments, the top hat 2430 may be composed of a conductive material. For example, the top hat 2430 may be formed by stamping a thin sheet of a conductive material such as copper or aluminum. In certain embodiments, the top hat 2430 may be composed of a combination of a dielectric material and a conductive material. For example, the top hat 2430 may be composed of a dielectric disk with copper plating on its surface at its shortest longitudinal portion.

[0373] In certain embodiments, the top hat 2430 may be fitted onto the first radiator. For example, the top hat 2430 may be bonded to the first radiator with epoxy resin. In certain embodiments, the top hat 2430 may be fixed to the first radiator. For example, the top hat 2430 may be fastened to the dielectric block 2410 to prevent longitudinal or radial movement of the first radiator. In certain embodiments, the top hat 2430 may be fitted onto the dielectric block 2410 or fixed by the dielectric block 2410. For example, the top hat 2430 may be bonded to one or more edges of the dielectric block 2410 at its longest longitudinal portion with epoxy resin. As another example, the top hat 2430 may be fastened to the dielectric block 2410 with nylon screws.

[0374] As shown in Figure 24, the dielectric jacket 2440 extends longitudinally between the longest longitudinal portion of the second radiator and the shortest longitudinal portion of the first radiator. As shown in Figure 24, the dielectric jacket 2440 fits radially outside the pin 2445 and extends radially to the outer conductor of the transmission line. In certain embodiments, the dielectric jacket 2440 may extend radially beyond the outer conductor of the transmission line. In certain embodiments, the dielectric jacket 2440 may be a standalone component. For example, the dielectric jacket 2440 may be a ring-shaped or donut-shaped dielectric inserted between the first and second radiators during the assembly of the antenna 2400. In certain embodiments, the dielectric jacket 2440 may be an extension of the dielectric in the transmission line. In certain embodiments, the dielectric jacket 2440 may be integrated into the dielectric pocket 2450. For example, the dielectric pocket 2450 may be additively manufactured such that the radial minimum of the dielectric pocket 2450 extends to the radial maximum of the pin 2455. In certain embodiments, the dielectric jacket 2440 may be omitted from the antenna 2400. Including the dielectric jacket 2440 in the antenna 2400 may have one or more advantages, including fixing the pin 2455, precisely controlling the isolation between the first and second radiators, and improving power operation.

[0375] The dielectric pocket 2450 extends radially from the maximum radius of the dielectric jacket 2440 to the minimum radius of the dielectric mass 2410, as shown in Figure 24. In certain embodiments, the dielectric pocket 2450 may be composed of free space or air. In certain embodiments, the dielectric pocket 2450 may be composed of a dielectric material. The dielectric pocket 2450 may be formed from the same or similar material or material composition as any dielectric mass disclosed herein. In certain embodiments, the dielectric pocket 2450 may have a different dielectric constant than the dielectric jacket 2440 and the dielectric mass 2410. In certain embodiments, the dielectric constant of the dielectric pocket 2450 may exceed the effective dielectric constant of the dielectric mass 2410. In certain embodiments, the dielectric constant of the dielectric mass 2410 may exceed the effective dielectric constant of the dielectric pocket 2450. In certain embodiments, the dielectric constant of the dielectric pocket 2450 may fall between the dielectric constant of the dielectric jacket 2440 and the dielectric constant of the dielectric mass 2410. In certain embodiments, inserting a dielectric pocket 2450 between the dielectric jacket 2440 and the dielectric block 2410 may have one or more advantages, including improving the fidelity of transmitting and receiving broadband signals through the antenna 2400, facilitating the matching of the antenna 2400, fabricating the dielectric block 2410 as a homogeneous block, and reducing the weight of the antenna 2400.

[0376] The first radiator 2405 is fitted radially into the dielectric mass 2410, as shown in Figure 24, and presents a conductive surface on the first radial inner surface of the dielectric mass 2410. The first radiator 2405 may also present a conductive surface at one or more edges between the first radial inner surface and the non-conductive aperture surface 2420. The first radiator 2405 may also present a conductive surface on a pin extending from the transmission line to the antenna 2400. In Figure 24, the first radiator 2405 is shown as a solid conductive mass (e.g., machined from a block of aluminum or copper). The first radiator 2405 may, in accordance with the topology of the other components in the antenna 2400 shown in Figure 24, have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions in the antenna as any other first radiator disclosed herein. The first radiator 2405 can be formed in accordance with the same or similar methods, operations, steps, parameters, and principles as any other first radiator disclosed herein, in accordance with the antenna 2400 topology shown in Figure 24.

[0377] The first radiator 2405 may extend longitudinally from the dielectric jacket 2440 to the maximum longitudinal portion of the dielectric mass 2410. In certain embodiments, the first radiator 2405 may extend from the inner conductor of the transmission line (e.g., a pin extending from the transmission line) to the maximum longitudinal portion of the dielectric mass 2410. The first radiator 2405 may be azimuthally uniform or radially symmetric. In certain embodiments, the first radiator 2405 may be symmetric. The first radiator 2405 may extend radially from the inner conductor of the transmission line to one or more edges of the dielectric mass 2410. In certain embodiments, the first radiator 2405 may extend to the maximum longitudinal radius of the dielectric mass 2410 (e.g., to the non-conductive aperture surface 2420). In certain embodiments, the first radiator 2405 may include a convex surface, a concave surface, or both convex and concave surfaces.

[0378] In certain embodiments, the first radiator 2405 may be fitted into the first radial inner surface during the fabrication of the antenna. For example, the first radiator 2405 may be machined from a conductive material and bonded to the first radial inner surface of the dielectric mass 2410 with epoxy resin. As another example, the first radiator 2405 may be formed by electrolytic emission of a conductor onto a dielectric base, inserted into a cavity on the radially inward side of the first radial inner surface of the dielectric mass 2410, and secured by the dielectric mass 2410 and the top hat 2430. In embodiments without a dielectric pocket 2450, the first radiator 2405 may be formed directly on the first radial inner surface. For example, the first radiator 2405 may be formed by spraying a conductive ink or dispersion onto the first radial inner surface.

[0379] In certain embodiments, the first radiator 2405 may be electrically coupled to a transmission line. For example, the first radiator 2405 may be soldered, welded, or joined to a pin extending from the center conductor of the transmission line. As another example, a pin extending from the center conductor of a coaxial connector may be press-fitted into the first radiator 2405.

[0380] In certain embodiments, the first radiator 2405 may be fitted to or electrically coupled to the top hat 2430. For example, the first radiator 2405 may be fixed within the dielectric mass 2410 by the top hat 2430 fastened to the dielectric mass 2410. In another example, the first radiator 2405 may be conductively bonded with epoxy resin to a conductive top hat 2430 that prevents current from flowing radially inside the first radiator 2405 in its maximum longitudinal dimension.

[0381] In certain embodiments, the maximum radial dimension of the first radiator 2405 may exceed the minimum radial dimension of the nonconductive aperture surface 2420. Reducing the minimum radial dimension of the nonconductive aperture surface 2420 may offer the advantages of thinning the dielectric mass 2410, reducing the weight of the antenna 2400, or increasing the operating bandwidth of the antenna 2400. In certain embodiments, the minimum radial dimension of the nonconductive aperture surface 2420 may exceed the maximum radial dimension of the first radiator 2405 (for example, as shown in Figure 24), or it may exceed the maximum radial dimension of any edge on the first radiator 2405 and the dielectric mass 2410. Increasing the thickness of the dielectric mass 2410 may have the advantages of lowering the lowest operating frequency of the antenna 2400, improving the return loss of the antenna 2400 near the lowest operating frequency, or controlling the gain or azimuthal uniformity of the radiation pattern at a particular frequency.

[0382] In certain embodiments, the first radiator 2405 may interface with a dielectric pocket 2450. In certain embodiments, the dielectric pocket 2450 may be part of a cavity on the radially inward side of the dielectric mass 2410, and the dielectric pocket 2450 may be defined by inserting the first radiator 2405 (together with the second radiator) into the cavity. In certain embodiments, the dielectric pocket 2450 may be composed of dielectric material such that, after the dielectric pocket 2450 is inserted radially into the dielectric mass 2410, the first radiator 2405 is assembled to the antenna 2400. In certain embodiments, the dielectric pocket 2450 may include, or be composed of, an adhesive for bonding the first radiator 2405 to the antenna 2400.

[0383] The second radiator 2415 is fitted radially into the dielectric mass 2410, as shown in Figure 24, and presents a conductive surface on the second radial inner surface of the dielectric mass 2410. The second radiator 2415 may also present a conductive surface at one or more edges between the second radial inner surface and the non-conductive aperture surface 2420. In Figure 24, the second radiator 2415 is shown as a solid conductive mass (e.g., machined from a block of aluminum or copper) having a cylindrical hole for fitting into a transmission line. The second radiator 2415 may, in accordance with the topology of the other components in the antenna 2400 shown in Figure 24, have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions in the antenna as any other second radiator disclosed herein. The second radiator 2415 may be formed in accordance with the same or similar methods, operations, steps, parameters, and principles as any other first radiator disclosed herein, in accordance with the topology of the antenna 2400 shown in Figure 24. The second radiator 2415 may be formed in accordance with the same or similar methods, operations, steps, parameters, and principles as the first radiator 2405, and may be assembled to or integrated with the antenna 2400 in accordance with the same or similar methods, operations, steps, parameters, and principles as the first radiator 2405.

[0384] The second radiator 2415 may extend longitudinally and radially from the outer conductor of the transmission line to one or more edges or nonconductive aperture surfaces 2420. In certain embodiments, the second radiator 2415 may extend longitudinally from the dielectric jacket 2440 to the minimum longitudinal portion of the dielectric mass 2410. The second radiator 2415 may extend radially from the outer conductor of the transmission line to one or more edges of the dielectric mass 2410. In certain embodiments, the second radiator 2415 may extend to the maximum longitudinal radius of the dielectric mass 2410. In certain embodiments, the second radiator 2415 includes convex, concave, or both convex and concave surfaces. The second radiator 2415 may be azimuthally uniform or radially symmetric. In certain embodiments, the second radiator 2415 may be symmetric.

[0385] In certain embodiments, the second radiator 2415 may be electrically coupled to a transmission line. For example, the second radiator 2415 may be soldered, welded, or joined to the outer conductor of the transmission line. As another example, the conductive surface of the second radiator 2415 may function as the outer conductor of the transmission line (for example, as shown in Figure 24, the conductive surface of the second radiator 2415 may be mated to a dielectric "candlestick" extending longitudinally from a coaxial connector). Coupled the second radiator 2415 to the transmission line excites an RF current in the second radiator 2415 over a wide bandwidth.

[0386] In certain embodiments, the second radiator 2415 may be mated to or electrically coupled to a ground plane. For example, the second radiator 2415 may be fixed within the dielectric block 2410 by a ground plane fastened to the dielectric block 2410. As another example, the second radiator 2415 may be electrically bonded with epoxy resin to a conductive ground plane that prevents current from flowing radially inside the second radiator 2415 in its minimum longitudinal dimension.

[0387] In certain embodiments, the maximum radial dimension of the second radiator 2415 may exceed the minimum radial dimension of the nonconductive aperture surface 2420. In certain embodiments, the minimum radial dimension of the nonconductive aperture surface 2420 may exceed the maximum radial dimension of the second radiator 2415 and any edge on the dielectric mass 2410.

[0388] In certain embodiments, the second radiator 2415 may interface with a dielectric pocket 2450. In certain embodiments, the dielectric pocket 2450 may be part of a cavity on the radially inward side of the dielectric mass 2410, and the dielectric pocket 2450 may be defined by inserting the second radiator 2415 (together with the first radiator 2405) into the cavity. In certain embodiments, the dielectric pocket 2450 may be composed of a dielectric material. For example, the second radiator 2415 may be assembled to the antenna 2400 after the dielectric pocket 2450 has been inserted radially into the dielectric mass 2410. As another example, the second radiator 2415 may be epoxy-bonded to the dielectric mass 2410 or the ground plane 2425, providing a structure to support the dielectric pocket 2450 during the assembly of the antenna 2400. In certain embodiments, the dielectric pocket 2450 may include or consist of an adhesive for bonding the second radiator 2415 to the antenna 2400.

[0389] As shown in Figure 24, the ground plane 2425 extends radially beyond the radial maximum of the antenna 2400 and is a conductive surface that shields the transceiver's circuits or other devices from the antenna 2400. As can be seen from a comparison of Figures 13B, 16B, 19B, and 24, the ground plane 2425 in antenna 2400 has substantially the same structure and function as the ground plane 1335 in antenna 1300, the ground plane 1635 in antenna 1600, and the ground plane 1935 in antenna 1900. The ground plane 2425 in the antenna may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as the ground plane 1335, the ground plane 1635, or the ground plane 1935. For example, the ground plane 2425 may extend radially from the outer conductor of the transmission line to the radial maximum of the antenna 2400. Ground plane 2425 can be formed in the same or similar manner, operation, steps, parameters, and principles as ground plane 1335, ground plane 1635, or ground plane 2425.

[0390] Transmission line 2435 may be any suitable transmission line for transmitting and receiving RF energy. Transmission line 2435 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as transmission line 1345, transmission line 1645, or transmission line 1945, in accordance with the antenna 2400 topology as shown in Figure 24. The dielectric jacket of transmission line 2435 may extend longitudinally beyond the second radiator 2415 and terminate at the first radiator 2405. In certain embodiments, the pins of transmission line 2435 may have the same longitudinal spread as the dielectric jacket, extend longitudinally beyond the second radiator 1915, and terminate at the first radiator 1905.

[0391] Pin 2445 may extend longitudinally from the transmission line 2435 to the first radiator 2405, centered on the radial axis of symmetry. In certain embodiments, the radially outer portion of pin 2445 may be mated to the dielectric jacket 2440. In certain embodiments, pin 2445 electrically couples the first radiator 2405 to the transmission line 2445. The first radiator 2405 may be soldered, welded, or joined to pin 2445. As another example, pin 2445 may be press-fitted into the first radiator 2405. In certain embodiments, pin 2445 may extend longitudinally beyond the dielectric jacket 2440 into or through the first radiator 2405. For example, although not shown in Figure 24, pin 2445 may extend longitudinally through the first radiator 2405 and be soldered radially into the first radiator 2405 such that the solder joint is accessible in a cavity on the radially inward side of the first radiator 2405.

[0392] As shown in Figure 24, antenna 2400 has two features not shown in Figures 13, 16, and 19: a top hat 2430 and a dielectric pocket 2450. The top hat 2430 and the dielectric pocket 2450 may be implemented together or separately. The dielectric pocket 2450 can extend the range of achievable radio performance (distortion reduction, improved impedance matching, or both). The top hat 2430 can fix the first radiator 2405 without substantially affecting radio performance.

[0393] Antenna 2400 may have the same or similar structure, components, elements, configurations, features, interfaces, parameters, or functions as those of other embodiments disclosed herein, conforming to the topology of Antenna 2400 shown in Figure 24. Antenna 2400 may be formed in the same or similar manner, operation, steps, parameters, and principles as those of other antennas disclosed herein.

[0394] Figures 25A to 25C show cross-sectional views of exemplary top-hat topologies in an antenna. An antenna 2400 having a top hat 2430 may be implemented according to any of Figures 25A to 25C. Similarly, the top-hat topologies of Figures 25A to 25C may be implemented in other antenna embodiments disclosed herein without substantially affecting radio performance or antenna size.

[0395] Figure 25A shows a first topology for fitting the top hat to the dielectric mass. The top hat 2520 may be formed as a separate component from the dielectric mass 2510. As shown in Figure 25A, the top hat 2520 may be longitudinally fixed to the dielectric mass 2510 through or at the edge at the maximum longitudinal portion of the dielectric mass 2510. For example, the top hat 2520 may be fixed to the dielectric mass 2510 by nylon screws, oriented longitudinally (coaxial with Z), through the edge at the maximum longitudinal portion of the dielectric mass 2510. In another example, the top hat 2520 may be bonded with epoxy resin to the edge at the maximum longitudinal portion of the dielectric mass 2510. The top hat 2520 may be fitted to the dielectric mass 2510 by several methods, including joining, sintering, fusion, fastening, or similar methods. The top hat 2520 may have the same or similar structure, features, or functions as the top hat 2430.

[0396] Figure 25B shows a second topology for mating the top hat to the dielectric mass. The top hat 2540 may be formed as a separate component from the dielectric mass 2530. The lip 2550 may be integrated with the dielectric mass 2530. In certain embodiments, the dielectric mass 2530 (specifically, the lip 2550) may extend longitudinally beyond the first radiator. As shown in Figure 25B, the top hat 2540 may be radially fixed to the dielectric mass 2530 through the lip 2550 near the maximum longitudinal portion of the dielectric mass 2530, or in the lip 2550. For example, the top hat 2540 may be oriented radially (coaxially with X or Y) by nylon screws and fixed to the dielectric mass 2530 through the lip 2550 near the maximum longitudinal portion of the dielectric mass 2530. In another example, the top hat 2540 may be bonded to the lip 2550 with epoxy resin. The top hat 2540 can be fitted into the dielectric mass 2530 by several methods, including joining, sintering, fusion, fastening, or similar methods. The top hat 2540 may have the same or similar structure, features, or functions as the top hat 2430. Fixing the top hat to the dielectric mass in a lip integrated with the dielectric mass may have one or more advantages, including maintaining the symmetry of the antenna, increasing the strength of the antenna or top hat against shear stress (in the XY plane), and inserting fasteners on the outside of the non-conductive aperture surface to avoid RF energy distortion or interference by RF energy.

[0397] Certain embodiments may combine features from both Figures 25A and 25B. For example, a top hat may be fastened to a dielectric mass having one or more lips in both the longitudinal and radial directions. A radially symmetric dielectric mass may have multiple lips (e.g., four lips, each covering an azimuth of 60°), and the top hat may be radially symmetric such that a portion of the top hat has the same maximum radius as the first radiator, and the other portion of the top hat has the same maximum radius as the dielectric mass. The top hat may be radially fastened to the multiple lips in a top hat portion having the same radial extension as the first radiator, and longitudinally fastened to the dielectric mass in a top hat portion having the same radial extension as the dielectric mass.

[0398] In certain embodiments, fixing the top hat to the dielectric mass also fixes the first radiator. In certain embodiments, the top hat may also be fixed to the first radiator. For example, the top hat may be bonded to the first radiator and fastened to the dielectric mass. In certain embodiments, a conductive top hat may be fastened to the first radiator using conductive screws. In certain embodiments, the top hat may be fixed to the dielectric mass only.

[0399] In certain embodiments, the top hat can prevent longitudinal movement of the first radiator. In certain embodiments, the dielectric mass can prevent radial movement of the first radiator, either alone or in combination with the top hat. In certain embodiments, the dielectric mass prevents longitudinal or radial movement of the second radiator (together with the ground plane). By fixing the radiators without interfering with or requiring modification of the first or second conductive surface, advantageous RF performance can be obtained, reducing distortion and increasing bandwidth.

[0400] Figure 25C shows a third topology for securing the first radiator. As shown in Figure 25C, the dielectric mass 2560 may comprise an integrated rim 2570. The opening surface 2580 may be located radially inward of the integrated rim 2570. The integrated rim 2570 extends radially inward such that the maximum radius of the first radiator 2565 exceeds the minimum radius of the integrated rim 2570. As shown in Figure 25C, the first radiator 2565 may be longitudinally inserted into the dielectric mass 2560 below the integrated rim 2570 through the opening surface 2580 at the maximum longitudinal portion of the dielectric mass 2560. In certain embodiments, the dielectric mass 2560 may be bent near the integrated rim 2570 to allow insertion of the first radiator 2565. In certain embodiments, both the dielectric mass 2560 and the first radiator 2565 may be bendable to facilitate insertion. In certain embodiments, the dielectric mass 2560 may bend based on the rigidity of the dielectric mass material or features (such as cavities or thinning to allow bending) in the dielectric mass first radiator 2565. When the first radiator 2565 is inserted into the dielectric mass 2560, the integrated rim 2570 grips and secures the first radiator 2565. The integrated rim 2570 may extend radially inward as permitted by the bending of the dielectric mass 2560 to accommodate the insertion of the first radiator 2565. In certain embodiments, the top hat is positioned on the opening surface 2580 at the widest longitudinal portion of the dielectric mass 2560 and may be secured to the dielectric mass or the first radiator according to any of the methods described herein.

[0401] Figure 26 shows the overall antenna 2400 in the elevation plane (ZY or ZX) and azimuth plane (XY) from 1 to 9 fL. 12The radiation pattern is shown. As shown in the elevation views of Figures 26A and 26B, antenna 2400 maintains a horizontal beam including a radiating horizontal line (θ=90°) over a frequency band of 1–6 fL. In certain embodiments, antenna 2400 can transmit and receive a beam including the horizontal line over a 6:1 pattern bandwidth. Although not shown in Figure 26, the radiation pattern of antenna 2400 in the azimuthal plane (XY, θ=90°) is substantially uniform in azimuthal angles over a 6:1 pattern bandwidth (1–6 fL). Antenna 2400 can maintain substantially uniform gain in azimuthal angles to the same extent as antennas 1300, 1600, or 1900. 12 The performance shown in Figure 26 pertains to antenna 2400, which has a ground plane with the same maximum ...

Claims

1. A radially symmetric dielectric unit, A first conductive surface having both a convex and a concave surface on the first radial inner surface of the dielectric unit, A second conductive surface extending radially outward from the radial symmetry axis, wherein the second conductive surface is inclined with respect to the radial symmetry axis, A nonconductive aperture surface on the radially outer surface of the dielectric unit, wherein the first conductive surface and the second conductive surface define a dielectric mass that extends radially toward the nonconductive aperture surface and terminates at the nonconductive aperture surface. A radially symmetric dielectric unit comprising An antenna equipped with this feature.

2. The antenna according to claim 1, wherein the dielectric unit is configured to instantaneously transmit and receive a radio signal over a single instantaneous bandwidth of 10:

1.

3. The antenna according to claim 1, wherein the dielectric unit is configured to transmit and receive radio signals over an efficiency bandwidth of 10:

1.

4. The antenna according to claim 1, wherein the dielectric unit is configured to transmit and receive radio signals over a 10:1 bandwidth, and the 10:1 bandwidth comprises a plurality of instantaneous frequency bands, each of which has a bandwidth that is a multiple of the lowest operating frequency.

5. The antenna according to claim 1, wherein the maximum radius of the dielectric unit does not exceed one-tenth of the minimum operating wavelength at which the return loss of the antenna achieves or exceeds 6 dB.

6. The antenna according to claim 1, wherein the maximum height of the dielectric unit does not exceed one-sixth of the minimum operating wavelength at which the return loss of the antenna achieves or exceeds 6 dB.

7. The antenna according to claim 1, wherein the first conductive surface and the second conductive surface are arranged on the dielectric mass to form the dielectric unit as a single unit without the conductive mass.

8. The antenna according to claim 1, wherein the first conductive surface has a conical angle of 50 to 70 degrees from the radial symmetry axis.

9. The antenna according to claim 1, wherein the dielectric unit is configured to prevent direct current flow between the first conductive surface and the second conductive surface.

10. A radially symmetric transmission line capable of transmitting a signal to the dielectric unit and receiving a signal from the dielectric unit. The antenna according to claim 1, further comprising the following:

11. The process involves forming a radially symmetric dielectric unit, wherein the radially symmetric dielectric unit is A first radial inner surface having both a convex and a concave surface, A second radial inner surface extending radially outward from the radial symmetry axis, wherein the second radial inner surface is inclined with respect to the radial symmetry axis, A nonconductive aperture surface on the radially outer side of the dielectric unit, wherein the first dielectric surface and the second dielectric surface define a dielectric mass that extends radially toward the nonconductive aperture surface and terminates at the nonconductive aperture surface. To be equipped with, to form, Placing a first conductive surface on the first dielectric surface, Placing a second conductive surface on the second dielectric surface, wherein the dielectric mass, the first conductive surface, and the second conductive surface form a dielectric unit, and the second conductive surface is placed on the second conductive surface. Methods that include...

12. The method according to claim 11, wherein the dielectric unit is configured to instantaneously transmit and receive a radio signal over a single instantaneous bandwidth of 10:

1.

13. The method according to claim 11, wherein the dielectric unit is configured to transmit and receive radio signals over an efficiency bandwidth of 10:

1.

14. The method according to claim 11, wherein the dielectric unit is configured to transmit and receive radio signals over a 10:1 bandwidth, and the 10:1 bandwidth includes a plurality of instantaneous frequency bands, each of which has a bandwidth that is a multiple of the lowest operating frequency.

15. The method according to claim 11, wherein the maximum radius of the dielectric unit does not exceed one-tenth of the minimum operating wavelength.

16. The method according to claim 11, wherein the maximum height of the dielectric unit does not exceed one-sixth of the minimum operating wavelength.

17. The dielectric unit is fitted into a ground plane that defines the azimuthal plane. The method according to claim 11, further comprising:

18. The method according to claim 11, wherein the first conductive surface has a conical angle of 50 to 70 degrees from the radial symmetry axis.

19. Receiving the signal from the dielectric unit using a radially symmetric transmission line. The method according to claim 11, further comprising:

20. The process involves forming a radially symmetric dielectric mass, wherein the dielectric mass is A first radial inner surface having both a convex surface and a concave surface on the first radial inner surface of the dielectric mass, A second radial inner surface extending radially outward from the radial symmetry axis, wherein the second radial inner surface is inclined with respect to the radial symmetry axis, A nonconductive aperture surface on the radially outer side of the dielectric mass, wherein the dielectric mass is configured to instantaneously transmit and receive a wireless signal over a single instantaneous bandwidth of 10:

1. to provide, to form Methods that include...

21. The first conductive surface is placed on the first radial inner surface, The arrangement of the second conductive surface on the second radial inner surface, wherein the dielectric mass, the first conductive surface, and the second conductive surface form a dielectric unit as a single unit without the conductive mass. The method according to claim 20, further comprising:

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