Power amplifier circuit, communication module, and communication device

Abstract

Embodiments of the present application relate to the technical field of terminals. Provided are a power amplifier circuit, a communication module, and a communication device. The power amplifier circuit comprises a power divider, a coupling unit, a first reactance unit, a first power amplification unit, and a signal amplification unit. The power divider is configured to decompose a radio frequency signal into a first signal and a second signal. The first signal is transmitted to a control end of the signal amplification unit by means of an input port and an isolation port of the coupling unit and the first power amplification unit, such that load impedance of the signal amplification unit is negatively correlated with input power of the radio frequency signal during power back-off. The second signal is amplified by means of the signal amplification unit and then is outputted. A phase shift of the first signal at the coupling unit is related to reactance at a fourth port. The first reactance unit is configured to adjust the reactance at the fourth port. In this way, phase adjustment and amplitude adjustment of the first signal are decoupled by means of the coupling unit and the reactance unit, thereby reducing the design difficulty and debugging difficulty of the power amplifier circuit.

Description

Power amplifier circuit, communication module and communication device

[0001] The present application claims priority to the Chinese patent application No. 202411155655.6, filed on August 22, 2024, and entitled "Power amplifier circuit, communication module and communication device", the content of which is incorporated herein by reference in its entirety. TECHNICAL FIELD

[0002] The present application relates to the technical field of terminal, and in particular to a power amplifier circuit, a communication module and a communication device. BACKGROUND

[0003] In order to improve the utilization rate of spectrum and the reliability of communication, the modulation mode of radio frequency signal is more and more complex, and the peak-to-average power ratio (PAPR) of radio frequency signal is higher and higher. In order to meet the linearity requirement of radio frequency signal power amplification, the power amplifier usually works in a power backoff state.

[0004] Compared with the conventional power amplifier circuit composed of a single structure of power amplifier (for example, only including an AB class power amplifier), the power amplifier circuit of load modulation structure has higher efficiency in the power backoff state.

[0005] However, the power amplifier circuit of load modulation structure has high debugging difficulty. SUMMARY

[0006] Embodiments of the present application provide a power amplifier circuit, a communication module and a communication device, which are applied to the technical field of terminal. The coupler is applied to the power amplifier circuit of load modulation structure to reduce the debugging difficulty of the power amplifier circuit.

[0007] In a first aspect, the embodiments of the present application provide a power amplifier circuit. The power amplifier circuit comprises a power divider, a first coupling unit, a first reactance unit, a first power amplification unit and a signal amplification unit. The power divider comprises a first port, a second port and a third port. The first coupling unit comprises a first input port, a first isolation port, a fourth port and a fifth port. The first port is configured to input a radio frequency signal. The second port is connected to the first input port. The first isolation port is connected to an input end of the first power amplification unit. An output end of the first power amplification unit is connected to a control end of the signal amplification unit. The fourth port is connected to one end of the first reactance unit. The other end of the first reactance unit is grounded. The fifth port is grounded. The third port is connected to an input end of the signal amplification unit. An output end of the signal amplification unit is configured to output an amplified radio frequency signal. The power divider is configured to decompose the radio frequency signal into a first signal and a second signal at the first port. The second port is configured to output the first signal. The third port is configured to output the second signal. The first coupling unit is further configured to adjust a phase of the first signal. The phase of the first signal at the first coupling unit is related to a reactance at the fourth port. The first reactance unit is configured to adjust the reactance at the fourth port. The first power amplification unit is configured to amplify the first signal. The signal amplification unit is configured to amplify the second signal. A load impedance of the signal amplification unit is negatively related to an input power of the radio frequency signal under control of the first signal at the input control end when power backoff occurs.

[0008] The first signal can correspond to signal A in the following description. The second signal can correspond to signal B in the following description.

[0009] The phase of the first signal is adjusted through the first coupling unit and the first reactance unit, thereby realizing load modulation of the signal amplification unit. In the process of adjusting the phase of the first signal at the first coupling unit through the first reactance unit, the amplitude of the first signal changes little. In this way, the phase shift change and loss change of the signal at the first coupling unit are decoupled, the influence of the phase modulation of the signal on the amplitude modulation of the signal is reduced, the prediction difficulty of the load impedance change of the signal amplification unit is reduced, the design difficulty of the power amplifier circuit of the load modulation structure is reduced, and the debugging difficulty is reduced.

[0010] In a possible implementation, the first reactance unit comprises a first capacitor.

[0011] In this way, the reactance of the first reactance unit can be adjusted by replacing the capacitor. The capacitor element is easy to disassemble, which facilitates debugging.

[0012] In a possible implementation, the power amplifier circuit further comprises a second reactance unit. One end of the second reactance unit is connected to the fifth port. The other end of the second reactance unit is grounded. The second reactance unit is configured to adjust the reactance at the fifth port to reduce the insertion loss of the first coupling unit.

[0013] In this way, the first signal can further include a signal reflected by the fifth port, and insertion loss of the first coupling unit can be reduced.

[0014] In a possible implementation, a difference between the reactance value of the first reactance unit and the reactance value of the second reactance unit is less than a preset threshold.

[0015] In this way, the reactance of the first reactance unit is close to or even the same as the reactance of the second reactance unit, a difference between a phase of a signal reflected by the coupling port to the isolation port and a phase of a signal reflected by the through port to the isolation port can be reduced, and insertion loss of the first coupling unit can be reduced.

[0016] In a possible implementation, the first reactance unit includes a first capacitor, and the second reactance unit includes a second capacitor, and a difference between a capacitance value of the first capacitor and a capacitance value of the second capacitor is less than a preset threshold.

[0017] In this way, the reactance adjustment of the first reactance unit and the reactance adjustment of the second reactance unit can be implemented by replacing the capacitors. The capacitive element is easy to disassemble, and debugging is facilitated.

[0018] In a possible implementation, the power amplifier circuit further includes a phase compensation unit located between the power divider and the signal amplification unit, and the phase compensation unit is configured to adjust a phase of the second signal, so that an absolute value of a difference between the first phase difference and the second phase difference is less than or equal to a first threshold. The first phase difference is a difference between the phase of the first signal at the first port and the phase of the second signal at the other end of the phase compensation unit when the radio frequency signal is of the first frequency. The second phase difference is a difference between the phase of the first signal at the first port and the phase of the second signal at the other end of the phase compensation unit when the radio frequency signal is of the second frequency.

[0019] The first threshold can be 1, 5, or any value, which is not limited herein.

[0020] The phase compensation unit can compensate for a difference in phase adjustment of the first coupling unit for signals of different frequencies, so that the power amplifier circuit maintains the phase difference between the first signal output by the first coupling unit and the second signal output by the phase compensation unit within a preset range when amplifying signals of different frequencies. In this way, wideband phase shifting of the power amplifier circuit can be implemented.

[0021] In a possible implementation, the signal amplification unit comprises: a second coupling unit, a second power amplification unit, a third power amplification unit, and a third coupling unit; the second coupling unit comprises: a second input port, a second isolation port, a sixth port, and a seventh port; the third coupling unit comprises: a third input port, a third isolation port, an eighth port, and a ninth port; the second input port is an input end of the signal amplification unit, the second isolation port is grounded, the sixth port is connected with an input end of the second power amplification unit, and an output end of the second power amplification unit is connected with the eighth port; the seventh port is connected with an input end of the third power amplification unit, an output end of the third power amplification unit is connected with the ninth port, and the third isolation port is a control end of the signal amplification unit; the third input port is used for outputting an amplified radio frequency signal; the second coupling unit is used for decomposing the second signal into a third signal and a fourth signal; the second power amplification unit is used for amplifying the third signal; the third power amplification unit is used for amplifying the fourth signal; and the third coupling unit is used for, under the control of the first signal, combining the third signal and the fourth signal to obtain the amplified radio frequency signal.

[0022] In this way, the power amplification of the second signal can be implemented by using two coupling units and two power amplification units, and the first signal can implement load modulation on the signal amplification unit in the power backoff.

[0023] In a second aspect, an embodiment of the present application provides a power amplifier circuit. The power amplifier circuit comprises: a first coupling unit, a first reactance unit, a first power amplification unit, and a signal amplification unit; the first coupling unit comprises: a first input port, a first isolation port, a fourth port, and a fifth port; the first input port is used for inputting a radio frequency signal, the first isolation port is connected with an input end of the first power amplification unit, and an output end of the first power amplification unit is connected with a control end of the signal amplification unit; the fourth port is connected with one end of the first reactance unit, and the other end of the first reactance unit is grounded; the fifth port is connected with an input end of the signal amplification unit, and an output end of the signal amplification unit is used for outputting an amplified radio frequency signal; the first coupling unit is used for decomposing the radio frequency signal into a first signal and a second signal at the first input port; wherein the first isolation port is used for outputting the first signal, and the fifth port is used for outputting the second signal; the first signal is related to the reactance at the fourth port in a phase shift of the first coupling unit; the first reactance unit is used for adjusting the reactance at the fourth port; the first power amplification unit is used for amplifying the first signal; and the signal amplification unit is used for amplifying the second signal; a load impedance of the signal amplification unit is negatively related to an input power of the radio frequency signal under the control of the first signal at the input control end in the power backoff.

[0024] The first signal can correspond to signal A in the following, and the second signal can correspond to signal B in the following.

[0025] The radio frequency signal can be divided into the first signal and the second signal by the first coupling unit. The first signal is phase adjusted in the first coupling unit, thereby realizing load modulation of the signal amplification unit. In the process of adjusting the phase shift of the first signal in the first coupling unit by the first reactance unit, the amplitude of the first signal changes little. In this way, the phase shift change and the loss change of the signal in the first coupling unit are decoupled, the influence of the phase modulation of the signal on the amplitude modulation of the signal is reduced, the prediction difficulty of the load impedance change of the signal amplification unit is reduced, the design difficulty of the power amplifier circuit of the load modulation structure is reduced, and the debugging difficulty is reduced.

[0026] In a possible implementation, the first reactance unit includes a first capacitor.

[0027] In this way, the reactance adjustment of the first reactance unit can be realized by replacing the capacitor. The capacitor element is easy to disassemble, and facilitates debugging.

[0028] In a possible implementation, the power amplifier circuit further includes a phase compensation unit located between the first coupling unit and the signal amplification unit. The phase compensation unit is configured to adjust the phase of the second signal, so that the absolute value of the difference between the first phase difference and the second phase difference is less than or equal to the first threshold. The first phase difference is the difference between the phase of the first signal at the first port and the phase of the second signal at the other end of the phase compensation unit when the radio frequency signal is at the first frequency. The second phase difference is the difference between the phase of the first signal at the first port and the phase of the second signal at the other end of the phase compensation unit when the radio frequency signal is at the second frequency.

[0029] The first threshold can be 1, 5 or any value, which is not limited here.

[0030] The phase compensation unit can compensate for the difference in the phase adjustment of the first coupling unit for signals of different frequencies, so that the phase difference between the first signal output by the first coupling unit and the second signal output by the phase compensation unit is maintained within a preset range when the power amplifier circuit amplifies signals of different frequencies. In this way, wideband phase shifting of the power amplifier circuit can be realized.

[0031] In a third aspect, an embodiment of the present application provides a communication module. The communication module includes: a radio frequency integrated circuit, and the power amplifier circuit in the first aspect, any possible implementation manner of the first aspect, the second aspect, or any possible implementation manner of the second aspect; the radio frequency integrated circuit is configured to output a radio frequency signal; and the power amplifier circuit is configured to amplify the radio frequency signal.

[0032] In a fourth aspect, an embodiment of the present application provides a communication device. The communication device includes: an antenna and the communication module in the third aspect or any possible implementation manner of the third aspect.

[0033] The communication module is configured to output the amplified radio frequency signal to the antenna; and the antenna is configured to transmit the amplified radio frequency signal.

[0034] It should be understood that the third aspect and the fourth aspect of the present application correspond to the technical solutions of the first aspect or the second aspect of the present application, and the beneficial effects obtained by each aspect and the corresponding feasible implementation manners are similar, which will not be described again. BRIEF DESCRIPTION OF DRAWINGS

[0035] FIG. 1 is a schematic diagram of the relationship between power backoff and efficiency provided by an embodiment of the present application;

[0036] FIG. 2 is a schematic diagram of the change of the load impedance of a power amplifier provided by an embodiment of the present application;

[0037] FIG. 3 is a schematic diagram of the structure of an LMBA in a possible design;

[0038] FIG. 4 is a schematic diagram of the change of the phase shift of signal A and the change of the insertion loss in a possible design;

[0039] FIG. 5 is a schematic diagram of the structure of a power amplifier circuit provided by an embodiment of the present application;

[0040] FIG. 6 is a schematic diagram of the change of the phase shift of signal A and the change of the insertion loss of the coupling unit 402 when the capacitance C2 changes;

[0041] FIG. 7 is a schematic diagram of the structure of a power amplifier circuit provided by an embodiment of the present application;

[0042] FIG. 8 is a schematic diagram of the structure of a phase compensation unit provided by an embodiment of the present application;

[0043] FIG. 9 is a schematic diagram of the change of the difference between the phase of signal A output by the coupling unit 402 and the phase of signal B input into the coupling unit 406 provided by an embodiment of the present application;

[0044] FIG. 10 is a schematic diagram of the structure of another power amplifier circuit provided by an embodiment of the present application;

[0045] FIG. 11 is a schematic diagram of the change of the phase shift of signal A and the change of the loss of signal A when the capacitance C4 changes provided by an embodiment of the present application;

[0046] FIG. 12 is a schematic diagram of the phase shift and the insertion loss of signal B in the coupling unit 902 provided by an embodiment of the present application;

[0047] FIG. 13 is a schematic diagram of the structure of a power amplifier circuit provided by an embodiment of the present application;

[0048] FIG. 14 is a schematic diagram of the structure of an electronic device provided by an embodiment of the present application;

[0049] FIG. 15 is a structural schematic diagram of a communication module provided by an embodiment of the present application. DETAILED DESCRIPTION

[0050] To facilitate clear description of the technical solutions of the embodiments of the present application, the following briefly introduces some terms and technologies involved in the embodiments of the present application:

[0051] 1. Power amplifier (PA)

[0052] The power amplifier amplifies the voltage and current of the input signal, thereby increasing the power output of the signal. Alternatively, it can be understood as power amplifying the radio frequency signal.

[0053] It should be noted that the working state of the power amplifier can be divided into a linear region and a nonlinear region. In the linear region, the output power of the power amplifier increases linearly with the increase of the input power; when the input power of the power amplifier further increases, the power amplifier enters the nonlinear region, and the output power of the power amplifier no longer increases with the increase of the input power. The output power of the power amplifier reaches saturation, at which time the efficiency of the power amplifier is the highest.

[0054] According to the category of the power amplifier, the PA can be divided into: class A power amplifier, class B power amplifier, class AB power amplifier, or class C power amplifier, etc.

[0055] Among them, the class A power amplifier is in a conducting state throughout the input signal period. When there is no input signal (which can also be understood as the power of the input signal being zero), the class A amplifier will also consume direct current power. It can also be understood that the conduction angle of the class A power amplifier is 360 degrees.

[0056] The class B power amplifier uses two amplifier elements for the positive half cycle and the negative half cycle of the input signal respectively, one for processing the positive half cycle and the other for processing the negative half cycle. When there is no input signal (which can also be understood as the power of the input signal being zero), the two elements are in an off state. It can also be understood that the conduction angle of the class B power amplifier is 180 degrees.

[0057] The class C power amplifier is conducting for a small part of the input signal period, usually less than 50% of the time. The working point of the class C amplifier is usually set near the cutoff region. It can also be understood that the conduction angle of the class C power amplifier is less than 180 degrees.

[0058] The class AB power amplifier combines the characteristics of class A and class B amplifiers, and the two amplifier elements are conducting in the positive half cycle and the negative half cycle of the input signal respectively, but there is a certain overlap conduction time near the zero crossing point. It can also be understood that the conduction angle of the class AB power amplifier is between 180 degrees and 360 degrees.

[0059] It can be understood that the class-A power amplifier is suitable for a scenario where the radio frequency signal is a small signal, the class-B power amplifier and the class-C power amplifier are suitable for a scenario where the radio frequency signal is a large signal, and the class-AB power amplifier is equivalent to the class-A power amplifier when the radio frequency signal is a small signal and is equivalent to the class-B power amplifier when the radio frequency signal is a large signal. Here, the small signal refers to a radio frequency signal with small power input to the power amplifier, and the large signal refers to a radio frequency signal with large power input to the power amplifier.

[0060] 3. Efficiency of the power amplifier

[0061] The efficiency of the power amplifier is used to represent the ability of the power amplifier to convert the input power into the output power. For example, the efficiency of the power amplifier can be the ratio of the output power to the input power of the power amplifier.

[0062] 4. Power backoff

[0063] The power backoff can be to reduce the output power of the power amplifier below its maximum output power. Or it can be understood as reducing the critical point (for example, the 1 dB compression point of the power amplifier) between the linear region and the nonlinear region of the power amplifier by a certain amplitude (for example, 6 dB, 10 dB, etc.).

[0064] In some embodiments, the power backoff is quantified in decibels (dB) to represent the amplitude of the reduction of the output power. For example, taking the maximum output power of a power amplifier as 30 decibel-milliwatts (dBm) and the power backoff of 3 dB as an example, the output power is reduced to 27 dBm.

[0065] 5. Nonlinear distortion

[0066] The nonlinear distortion can be understood as the nonlinear relationship between the signal output by the nonlinear device (for example, the power amplifier) and the signal input to the nonlinear device, resulting in signal distortion when the signal passes through the nonlinear device.

[0067] 6. Other terms

[0068] In the embodiments of the present application, the same items or similar items with basically the same functions and effects are distinguished by using "first", "second", etc. For example, the first chip and the second chip are only used to distinguish different chips, and do not limit the sequence. Those skilled in the art can understand that "first", "second", etc. do not limit the quantity and execution sequence, and "first", "second", etc. also do not necessarily mean different.

[0069] It should be noted that the terms "exemplary" and "for example" are used herein to mean "serving as an example, instance, or illustration," and not "preferred" or "advantageous over other examples." The usage of these terms in this application is not intended to convey any preference or advantage for the embodiments or examples described with such terms.

[0070] In the embodiments of the present application, "at least one" means one or more, and "multiple" means two or more. The "and / or" describes the association relationship of the associated objects, which means that there can be three relationships, for example, A and / or B, which can represent the following three cases: A exists alone, A and B exist together, and B exists alone, wherein A and B can be singular or plural. The character " / " generally represents an "or" relationship between the associated objects before and after it. "At least one of the following" or similar expressions means any combination of these items, including any combination of single or multiple items. For example, at least one of a, b, or c can represent a, b, c, a-b, a-c, b-c, or a-b-c, wherein a, b, and c can be single or multiple.

[0071] 7. Electronic device

[0072] The electronic device of the embodiments of the present applicationapplicationinclude a handheld device having a signal transmitting function, a vehicle-mounted device, etc. For example, some electronic devices are: a mobile phone, a tablet computer, a palm computer, a notebook computer, a mobile internet device (MID), a wearable device (for example, a smart watch, smart glasses, a smart bracelet, or smart jewelry, etc.), a virtual reality (VR) device, an augmented reality (AR) device, a wireless terminal in industrial control, a wireless terminal in self driving, a wireless terminal in remote medical surgery, a wireless terminal in a smart grid, a wireless terminal in transportation safety, a wireless terminal in a smart city, a wireless terminal in a smart home, a cellular phone, a cordless phone, a session initiation protocol (SIP) phone, a wireless local loop (WLL) station, a personal digital assistant (PDA), a handheld device with a wireless communication function, a computing device or other processing device connected to a wireless modem, a vehicle-mounted device, a terminal device in an internet of things (IoT) system, a terminal device in a 5G network, or a terminal device in a future evolved public land mobile network (PLMN), etc. The embodiments of the present application are not limited thereto.

[0073] The electronic device in the embodiments of the present applicationapplicationalso be referred to as: a terminal device, a user equipment (UE), a mobile station (MS), a mobile terminal (MT), an access terminal, a subscriber unit, a subscriber station, a mobile station, a mobile terminal, a remote station, a remote terminal, a mobile device, a user terminal, a terminal, a wireless communication device, a user agent, or a user apparatus, etc.

[0074] To improve the utilization rate of the spectrum and the reliability of communication, the modulation mode of the radio frequency signal in the communication system is more and more complex, and thus the peak-to-average ratio of the radio frequency signal increases. The increase of the peak-to-average ratioapplicationcause the power amplifier in the power amplifier circuit to work in a nonlinear region, and thus cause the nonlinear distortion of the power amplifier circuit.

[0075] The power amplifier in the power amplifier circuit enters a nonlinear region and the nonlinear distortion is reduced by means of power backoff.

[0076] However, the efficiency of the conventional power amplifier circuit (e.g., including only an AB class power amplifier) is low in the power backoff state. The conventional power amplifier circuit is composed of a single structure of power amplifier, for example, the conventional power amplifier circuit includes only an AB class power amplifier.

[0077] For example, FIG. 1 is a schematic diagram of the relationship between power backoff and efficiency provided by an embodiment of the present application. Taking the example of a conventional power amplifier circuit including a B class power amplifier or an AB class power amplifier, the efficiency change of the B class power amplifier under different power backoff values can be shown as curve 101 in FIG. 1, and the efficiency change of the AB class power amplifier under different power backoff values can be shown as curve 102 in FIG. 1.

[0078] As can be seen from FIG. 1, the efficiency of the conventional power amplifier circuit is negatively related to the power backoff value, and the higher the power backoff value is, the lower the efficiency of the power amplifier is.

[0079] It can be understood that in the power backoff state, the efficiency of the conventional power amplifier circuit is low, and the power consumption of the power amplifier circuit is high. In addition, the power amplifier circuit may emit a large amount of heat in the low efficiency state, and the heat dissipation pressure of the electronic device is large. The power amplifier circuit may be damaged by overheat due to the heat dissipation not in time in the case of working in the low efficiency for a long time, and the service life of the power amplifier circuit is reduced.

[0080] In some embodiments, the electronic device adopts a power amplifier circuit with a load modulation structure to amplify the radio frequency signal. Specifically, the power amplifier circuit with the load modulation structure can divide the radio frequency signal into signal A and signal B, signal A can adjust the phase and amplitude of the signal through the control signal unit, and signal B is amplified (power amplified) through the signal amplification unit. After adjusting the phase and amplitude, signal A can be input into the signal amplification unit from the control end of the signal amplification unit, so that the load impedance of the signal amplification unit is negatively related to the input power of the radio frequency signal in the power backoff, and then the efficiency of the signal amplification unit is improved, and the efficiency of the power amplifier circuit is improved.

[0081] Taking a load modulated balanced amplifier (LMBA) as an example, the control signal unit of the LMBA includes a power amplifier CA, and the signal amplification unit of the LMBA includes an input coupler, two power amplifiers BA, and an output coupler.

[0082] In a possible design, the LMBA works as follows: signal A can be transmitted to the isolation port of the output coupler after signal amplification by the power amplifier CA.

[0083] Signal B can be split into two orthogonal signals with equal amplitude (a phase difference of 90 degrees) by the input coupler, and the two orthogonal signals are amplified by the corresponding power amplifier BA and transmitted to the through port and the coupled port of the output coupler.

[0084] Through reasonable design of the size (which can also be understood as the amplitude) and phase of signal A transmitted to the isolation port of the output coupler, the load impedance of the two power amplifiers BA can be modulated, and the load impedance modulation of the signal amplification unit by the signal A transmitted by the control unit can be realized, so that the efficiency of the LMBA is improved.

[0085] It should be noted that the load impedance of the power amplifier is equal to the ratio of the output voltage to the output current, as shown in FIG. 2a. When the load impedance of the power amplifier is constant (i.e., the slope of the output voltage / output current is constant), the output voltage is small when the output current of the power amplifier is small, and the efficiency of the power amplifier is low. As shown in FIG. 2b, when the output current of the power amplifier is small, the output voltage of the power amplifier can be increased by increasing the load impedance of the power amplifier, so that the power amplifier can enter the saturation region more easily, thereby improving the efficiency of the power amplifier.

[0086] It can be understood that, compared with the conventional power amplifier structure, the power amplifier circuit with load modulation structure has higher efficiency in the backoff state. For example, taking the LMBA with load modulation structure as an example, the efficiency change of the LMBA under different power backoff can be shown in curve 103 in FIG. 1. When the power backoff value is less than -10 dB, the efficiency of the LMBA gradually increases as the power backoff decreases; when the power backoff is -10 dB, the efficiency of the LMBA reaches the highest; when the power backoff is between -10 dB and 0 dB, the efficiency of the LMBA first decreases and then increases as the power backoff decreases.

[0087] As can be seen from FIG. 1, compared with the conventional power amplifier circuit, the efficiency of the LMBA in the power backoff state is higher.

[0088] However, the design difficulty of the power amplifier circuit with load modulation structure in the possible design is high.

[0089] An exemplary power amplifier circuit in a load modulation structure is taken as an LMBA, and Fig. 3 is a schematic diagram of a structure of the LMBA in a possible design. As shown in Fig. 3, the LMBA includes a power divider 201, an LC phase-shifting unit 202, a power amplifier 203, a coupler 204, a power amplifier 205, a power amplifier 206, and a coupler 207. The control unit can include the LC phase-shifting unit 202 and the power amplifier 203, and the signal amplification unit can include the coupler 204, the power amplifier 205, the power amplifier 206, and the coupler 207.

[0090] The power divider 201 includes a port 1a, a port 1b, and a port 1c; the coupler 204 includes an input port 2a, a coupled port 2b, a through port 2c, and an isolated port 2d; and the coupler 207 includes an input port 3a, a coupled port 3b, a through port 3c, and an isolated port 3d.

[0091] As shown in Fig. 3, the port 1a of the power divider 201 is configured to input a radio frequency signal; the port 1b of the power divider 201 is connected to one end of the LC phase-shifting unit 202, and the port 1c of the power divider 201 is connected to the input port 2a of the coupler 204. The other end of the LC phase-shifting unit 202 is connected to the input end of the power amplifier 203, and the output end of the power amplifier 203 is connected to the isolated port 3d of the coupler 207; the coupled port 2b of the coupler 204 is connected to the input end of the power amplifier 205, and the output end of the power amplifier 205 is connected to the through port 3c of the coupler 207; the through port 2c of the coupler 204 is connected to the input end of the power amplifier 206, and the output end of the power amplifier 206 is connected to the isolated port 3d of the coupler 207; the input port 3a of the coupler 207 is configured to output an amplified radio frequency signal, and the isolated port 2d of the coupler 204 is grounded.

[0092] In the circuit shown in Fig. 3, the power divider 201 can divide the radio frequency signal input into the LMBA into two signals, which are processed by the control signal unit and the signal amplification unit, respectively.

[0093] Taking an example in which the power divider 201 divides the radio frequency signal into signal A and signal B, the signal A is phase-adjusted by the LC phase-shifting unit 202 and signal-amplified by the power amplifier 203, and then transmitted to the isolated port 3d of the coupler 207.

[0094] The signal B is decomposed into signal b1 and signal b2 by the coupler 204. The signal b1 is signal-amplified by the power amplifier 205 and then transmitted to the through port 3c of the coupler 207; and the signal b2 is signal-amplified by the power amplifier 206 and then transmitted to the coupled port 3b of the coupler 207. The amplitudes of the signal b1 and the signal b2 are equal, and the signal b1 and the signal b2 are orthogonal (the phase difference between the signal b1 and the signal b2 is 90 degrees).

[0095] The amplified signal A, the amplified signal b1 and the amplified signal b2 are combined into one signal output at the coupler 207.

[0096] It should be noted that the impedance of the through port 3c of the coupler 207 and the impedance of the coupled port 3b of the coupler 207 are both controlled by the amplified signal A. It can also be understood that the impedance of the through port 3c of the coupler 207 and the impedance of the coupled port 3b of the coupler 207 are both related to the amplitude and phase of the amplified signal A.

[0097] It can be understood that in the LMBA shown in FIG. 3, the amplitude and phase control of the amplified signal A is achieved by adjusting the LC phase shift unit 202, and the dynamic load matching of the signal amplification unit is achieved.

[0098] However, in the process of adjusting the LC phase shift unit 202, the phase shift of the signal A in the LC phase shift unit and the loss of the signal A in the LC phase shift unit will change, and then the phase and amplitude of the amplified signal A will change. Due to the change of the phase and amplitude of the amplified signal A, it is difficult to predict the change of the load impedance of the signal amplification unit, and it is difficult to achieve dynamic load matching, and the design of the LMBA is difficult.

[0099] In the embodiments of the present application, the phase shift of the signal in the LC phase shift unit can be understood as the difference between the phase of the signal output by the LC phase shift unit and the phase of the signal input into the LC phase shift unit. The loss of the signal in the LC phase shift unit can also be referred to as the insertion loss of the LC phase shift unit.

[0100] For example, the LC phase shift unit 202 shown in FIG. 3 includes one inductor and one capacitor. When the capacitance value of the capacitor C1 is adjusted, the phase of the amplified signal A changes, causing the load impedance of the signal amplification unit to change. In addition, the insertion loss of the LC phase shift unit 202 fluctuates greatly, and the amplitude of the amplified signal A also changes, causing the load impedance of the signal amplification unit to change.

[0101] For example, taking the N77 signal with a frequency range of 3.3 gigahertz (GHz) to 4.2 GHz as the radio frequency signal, the inductance value of the inductor L1 is 0.7 nanohenry (nH), and the capacitance value of the capacitor C1 is 0.5 picofarad (pF) and 0.9 pF. The insertion loss of the LC phase shift unit 202 and the phase shift of the signal A in the LC phase shift unit 202 are described.

[0102] As shown in FIG. 4, in the scenario of the capacitance C1 being 0.5 pf, the phase shift of the signal A at the LC phase shift unit can be as shown in the curve 301 in a of FIG. 4; in the scenario of the capacitance C1 being 0.9 pf, the phase shift of the signal A at the LC phase shift unit can be as shown in the curve 302 in a of FIG. 4; in the scenario of the capacitance C1 being 0.5 pf, the insertion loss of the LC phase shift unit can be as shown in the curve 303 in b of FIG. 4; in the scenario of the capacitance C1 being 0.9 pf, the insertion loss of the LC phase shift unit can be as shown in the curve 304 in b of FIG. 4.

[0103] As can be seen from FIG. 4, if the capacitance value is adjusted from 0.5 pf to 0.9 pf, the phase shift of the signal A at the LC phase shift unit changes between 10 degrees and 15 degrees, and the insertion loss of the LC phase shift unit changes between 0.4 dB and 0.7 dB.

[0104] As can be seen from FIGS. 3 and 4, when the capacitance value of the capacitance C1 changes, the phase shift of the signal A at the LC phase shift unit and the insertion loss of the LC phase shift unit both change. It can also be understood that, in the process of adjusting the phase of the signal A by adjusting the capacitance value of the capacitance C1, the insertion loss of the LC phase shift unit changes, so that the amplitude of the amplified signal A also changes, and thus the change of the load impedance of the signal amplification unit is difficult to predict, and the design of the LMBA is difficult and the debugging is difficult.

[0105] It can be understood that the LC phase shift unit 202 shown in FIG. 3 is only an example, and the LC phase shift unit 202 can be more complex, and the decoupling relationship between the amplitude and the phase of the amplified signal A makes the design of the LMBA difficult, and the design time is long and the debugging is difficult.

[0106] Therefore, the embodiments of the present application provide a power amplifier circuit, a communication module and a communication device. The phase of the signal transmitted in the control signal unit is adjusted by a coupler. Specifically, the isolation port of the coupler is connected with the power amplifier in the control signal unit, and the reactance unit is arranged at the through port or the coupling port of the coupler to adjust the phase of the signal output by the isolation port.

[0107] It should be noted that, in the process of adjusting the phase of the signal output by the isolation port by the reactance unit, the insertion loss of the coupler changes little, so that the amplitude of the signal output by the isolation port changes little. In this way, the phase shift change of the signal in the control signal unit and the insertion loss change (which can also be referred to as the loss change of the signal) of the control signal unit are decoupled, the influence of the phase modulation of the signal on the amplitude modulation of the signal is reduced, the prediction difficulty of the change of the load impedance of the signal amplification unit is reduced, and the design difficulty and the debugging difficulty of the power amplifier circuit of the load modulation structure are reduced.

[0108] For example, FIG. 5 is a structural schematic diagram of a power amplifier circuit provided by an embodiment of the present application. As shown in FIG. 5, the power amplifier includes a power divider 401, a coupling unit 402, a power amplification unit 403, a reactance unit 404, a reactance unit 405, a coupling unit 406, a power amplification unit 407, a power amplification unit 408, and a coupling unit 409.

[0109] The power divider 401 includes a port 4a, a port 4b, and a port 4c; the coupling unit 402 includes an input port 5a, a coupling port 5b, a through port 5c, and an isolation port 5d; the coupling unit 406 includes an input port 6a, a coupling port 6b, a through port 6c, and an isolation port 6d; and the coupling unit 409 includes an input port 7a, a coupling port 7b, a through port 7c, and an isolation port 7d.

[0110] As shown in FIG. 5, the port 4a of the power divider 401 is configured to input a radio frequency signal; the port 4b of the power divider 401 is connected to the input port 5a of the coupling unit 402, and the port 4c of the power divider 401 is connected to the input port 6a of the coupling unit 406.

[0111] The isolation port 5d of the coupling unit 402 is connected to the input end of the power amplification unit 403, and the output end of the power amplification unit 403 is connected to the isolation port 7d of the coupling unit 409; the through port 5c of the coupling unit 402 is connected to one end of the reactance unit 404, and the other end of the reactance unit 404 is grounded; and the coupling port 5b of the coupling unit 402 is connected to one end of the reactance unit 405, and the other end of the reactance unit 405 is grounded.

[0112] The coupling port 6b of the coupling unit 406 is connected to the input end of the power amplification unit 407, and the output end of the power amplification unit 407 is connected to the through port 7c of the coupling unit 409; the through port 6c of the coupling unit 406 is connected to the input end of the power amplification unit 408, and the output end of the power amplification unit 408 is connected to the isolation port 7d of the coupling unit 409; the input port 7a of the coupling unit 409 is configured to output an amplified radio frequency signal, and the isolation port 6d of the coupling unit 406 is grounded.

[0113] In the embodiment of the present application, the power divider 401 is configured to divide the radio frequency signal into two paths to obtain signal A and signal B. The power of the signal A and the signal B can be the same or different, which is not limited herein.

[0114] The coupling unit 402 is configured to adjust the phase of the signal A. The phase shift of the signal A at the coupling unit 402 is related to the reactance of the reactance unit 404 and the reactance of the reactance unit 405. Specifically, when the reactance of the reactance unit 404 or the reactance of the reactance unit 405 changes, the phase shift of the signal A at the coupling unit 402 also changes.

[0115] It should be noted that based on the coupling effect of the electromagnetic field, the coupling line in the coupler can couple the signal transmitted by the transmission line in the coupler and output the coupled signal from the coupling port; the uncoupled signal is output from the through port, and the reflected signal (for example, signal A) is output from the isolation port. The reflected signal can include the signal reflected by the coupling port and the signal reflected by the through port.

[0116] It can be understood that in the case where the reactance unit is arranged at the coupling port, the reactance unit can reflect part or all of the coupled signal to the isolation port. In the case where the reactance unit is arranged at the through port, the reactance unit can reflect part or all of the uncoupled signal to the isolation port.

[0117] Therefore, the phase of the reflected signal output at the isolation port is related to both the reactance at the coupling port and the reactance at the through port. Specifically, when the reactance at the coupling port changes, the phase of the reflected signal output at the isolation port changes; or when the reactance at the through port changes, the phase of the reflected signal output at the isolation port changes.

[0118] In the embodiment of the present application, by changing the reactance at the through port 5c and / or the reactance at the coupling port 5b, the phase change of the signal A output at the isolation port of the coupling unit 402 can be realized.

[0119] In the embodiment of the present application, the power of the signals output at the through port and the coupling port of the coupling unit 402 can be the same or different. The coupling unit 402 can be a coupler or any other device with the same function, which is not limited here.

[0120] For example, the coupling unit 402 can be a 3dB coupler. The power of the signals output at the through port and the coupling port of the 3dB coupler is the same.

[0121] The power amplification unit 403 is configured to amplify the signal A. The power amplification unit 403 can include one or more power amplification units, which are not limited here.

[0122] In some embodiments, the power amplification unit 403 works in class B or class C mode. When the power of the signal A is small, the power amplification unit 403 is not turned on; when the power of the signal A is large, the transistor in the power amplification unit 403 is in an open state, and the power amplification unit 403 amplifies the signal A.

[0123] The reactance unit 404 is configured to adjust the reactance of the through port 5c, so that the phase shift of the signal A transmitted through the coupling unit 402 changes, and then the phase of the signal A changes.

[0124] The reactance unit 404 can include one or more reactance elements, such as a capacitor, an inductor, or a magnetic bead, etc. No specific limitation is made herein. In some embodiments, the reactance unit 404 includes a capacitor. The capacitor is easy to disassemble and replace, facilitating debugging of the power amplifier circuit.

[0125] The reactance unit 405 is configured to adjust the reactance of the coupling port 5b, so that the phase shift of the signal A transmitted through the coupling unit 402 changes, and in turn the phase of the signal A changes.

[0126] The reactance unit 405 can include one or more reactance elements, such as a capacitor or an inductor or a magnetic bead, etc. No specific limitation is made herein.

[0127] In some embodiments, the reactance of the reactance unit 405 is less than or equal to a threshold value A from the reactance of the reactance unit 404. The threshold value A can be 0.1, 0.5, or any value, no specific limitation is made herein. In this way, the difference between the phase of the signal reflected from the coupling port to the isolation port and the phase of the signal reflected from the through port to the isolation port can be reduced, and the insertion loss of the coupling unit 402 can be reduced.

[0128] For example, the reactance unit 405 includes a capacitor C3, and the difference between the capacitance value of the capacitor C3 and the capacitance value of the capacitor C2 is less than the threshold value A. The threshold value A can be 0.1 pf, 0.5 pf, or any value, no specific limitation is made herein.

[0129] In this way, the capacitance value of the capacitor C3 is close to or even the same as the capacitance value of the capacitor C2, so that the reactance of the reactance unit 405 is close to or even the same as the reactance of the reactance unit 404, and the insertion loss of the coupling unit 402 is reduced.

[0130] In some embodiments, the coupling unit 402 is a 3dB coupler. In this way, the insertion loss of the coupling unit 402 can be reduced.

[0131] It can be understood that the reactance unit 404 and the reactance unit 405 can both adjust the phase of the signal A, and therefore, the power amplifier circuit can include either one of the reactance unit 404 and the reactance unit 405, or both of the reactance unit 404 and the reactance unit 405. No specific limitation is made herein.

[0132] The coupling unit 406 is configured to split the signal B into a signal b1 and a signal b2 at the input port 6a, and output the signal b1 from the coupling port 6b and output the signal b2 from the through port 6c. The signal b1 output by the coupling unit 406 and the signal b2 output by the coupling unit 406 are orthogonal.

[0133] The orthogonality can be understood as a phase difference of 90 degrees between two signals. In the embodiments of the present application, the orthogonality can be understood as a phase difference of 90 degrees between the signal b1 output by the coupling port 6b and the signal b2 output by the through port 6c; or can be understood as a difference of 90 degrees between the phase shift of the signal b1 at the coupling unit 406 and the phase shift of the signal b2 at the coupling unit 406 (the difference between the phase of the signal b2 at the through port and the phase at the input port). Wherein, the phase shift of the signal b1 at the coupling unit 406 is the difference between the phase of the signal b1 at the coupling port 6b and the phase at the input port 6a; the phase shift of the signal b2 at the coupling unit 406 is the difference between the phase of the signal b2 at the through port 6c and the phase at the input port 6a.

[0134] It should be understood that the orthogonality in the embodiments of the present application can be a standard orthogonality in a mathematical sense (for example, the phase difference between the signal b1 and the signal b2 output by the coupling unit 406 is 90 degrees), or can be an orthogonality within a certain error range. Taking an error range of plus or minus 1 degree as an example, when the phase difference between the signal b1 and the signal b2 output by the coupling unit 406 is between 89 degrees and 91 degrees, the signal b1 and the signal b2 are orthogonal.

[0135] The coupling unit 406 can be a coupler, or any other device with the same function, which is not limited here.

[0136] The power amplification unit 407 is configured to perform signal amplification on the signal b1; and the power amplification unit 408 is configured to perform signal amplification on the signal b2.

[0137] In some embodiments, the power amplification unit 407 can include one or more power amplifiers; and the power amplification unit 408 can include one or more power amplifiers, which are not limited here.

[0138] In some embodiments, the power amplification unit 407 and the power amplification unit 408 both work in an AB mode, a transistor in the power amplification unit 407 is in an open state, and the power amplification unit 407 amplifies the signal b1; a transistor in the power amplification unit 408 is in an open state, and the power amplification unit 408 amplifies the signal b2.

[0139] The coupling unit 409 is configured to combine the amplified signal b1 and the amplified signal b2 to obtain an amplified radio frequency signal. Wherein, the phase of the amplified signal b1 is affected by the impedance between the power amplification unit 407 and the coupling unit 409. And the impedance is affected by the phase and amplitude of the amplified signal A transmitted by the isolation port 7d.

[0140] The coupling unit 409 can be a coupler, or any other device with the same function, which is not limited here.

[0141] The working principle and efficiency of the power amplifier circuit shown in FIG. 5 are described as follows. Taking the power amplifier unit 403 working in the B mode, and the power amplifier units 407 and 408 working in the AB mode as an example, the working principle is as follows:

[0142] When the input power of the radio frequency signal is small, the power of the signal A is insufficient to turn on the transistor in the power amplifier unit 403, and the isolation port 7d of the coupling unit 409 presents an open circuit state, and the control signal unit does not perform load modulation on the signal amplification unit.

[0143] At this time, the power amplifier units 407 and 408 amplify the signals b1 and b2 respectively. Since the powers of the signals b1 and b2 are low, and the power amplifier units 407 and 408 work in the linear region, the efficiencies of the power amplifier units 407 and 408 are low, and the efficiency of the power amplifier circuit is low.

[0144] As the input power gradually increases, the powers of the signals A and B gradually increase, the efficiencies of the power amplifier units 407 and 408 gradually increase, and the efficiency of the power amplifier circuit gradually increases.

[0145] When the input power of the radio frequency signal reaches the power A, the power of the signal A triggers the power amplifier unit 403 to start working, and the amplified signal A is transmitted to the isolation port 7d of the coupling unit 409. The amplified signal A, the amplified signal b1 and the amplified signal b2 are superimposed, so that the output power of the power amplifier circuit is improved.

[0146] In addition, when the input power of the radio frequency signal reaches the power A, the control signal unit starts to perform load modulation on the signal amplification unit. It can also be understood that the amplified signal A starts to modulate the impedance at the through port 7c of the coupling unit 409 and the impedance at the coupling port 7b of the coupling unit 409.

[0147] As the input power of the radio frequency signal increases, the power of the amplified signal A gradually increases, so that the load impedance of the power amplifier unit 407 and the load impedance of the power amplifier unit 408 gradually decrease, and the efficiencies of the power amplifier units 407 and 408 can still maintain a high level, and the efficiency of the power amplifier circuit for power amplification can still maintain a high level.

[0148] When the input power of the radio frequency signal reaches power B, the power amplification units 403, 407 and 408 all reach saturation, and the power of the amplified radio frequency signal (which can also be referred to as the output power of the power amplifier circuit) reaches the maximum. Moreover, the load impedance of the power amplification units 407 and 408 is optimally matched with the source impedance, and the efficiency of the power amplifier circuit reaches the maximum.

[0149] It can be understood that the load impedance of the signal amplification unit in the power amplifier circuit provided by the embodiments of the present application is related to the amplitude and phase of the signal transmitted by the control signal unit. The amplitude and phase of the signal are related to the phase shift and insertion loss of the coupling unit 402. Therefore, the debugging difficulty of the power amplifier circuit shown in FIG. 5 is related to the change of the phase shift and the change of the insertion loss of the coupling unit 402.

[0150] The change of the phase shift and the change of the insertion loss of the coupling unit 402 will be described below in combination with FIG. 6.

[0151] For example, FIG. 6 is a schematic diagram of the change of the phase shift of the signal A at the coupling unit 402 and the change of the insertion loss of the coupling unit 402 when the capacitance C2 changes, according to the embodiments of the present application.

[0152] As shown in FIG. 6, in the scenario where the capacitance C2 is 1.5 pF, the phase shift of the signal A at the coupling unit 402 can be as shown in the curve 501 in FIG. 6a; in the scenario where the capacitance C2 is 2 pF, the phase shift of the signal A at the coupling unit 402 can be as shown in the curve 502 in FIG. 6a; in the scenario where the capacitance C2 is 1.5 pF, the insertion loss of the signal A at the coupling unit 402 can be as shown in the curve 503 in FIG. 6b; in the scenario where the capacitance C2 is 2 pF, the insertion loss of the signal A at the coupling unit 402 can be as shown in the curve 504 in FIG. 6b.

[0153] As can be seen from FIG. 6, if the capacitance value is adjusted from 1.5 pf to 2 pf, the change of the phase shift of the signal A at the coupling unit 402 is between 10 degrees and 15 degrees, and the change of the insertion loss of the coupling unit 402 is between 0.002 dB and 0.006 dB.

[0154] Compared with the LMBA shown in FIG. 3, in the process of adjusting the phase of the signal A, the change of the insertion loss of the coupling unit 402 in the power amplifier circuit shown in FIG. 5 is smaller, so that the change of the amplitude of the amplified signal A is smaller, and then the change of the load impedance of the signal amplification unit is easy to predict, and the design difficulty of the power amplifier circuit is small. In addition, the insertion loss of the coupling unit 402 is small, and the power loss is small.

[0155] On the basis of the embodiment shown in FIG. 5, the power amplifier circuit provided in the embodiment of the present application further comprises a phase compensation unit. The phase compensation unit is located on the signal amplification unit, for example, between the power divider 401 and the coupling unit 402. The phase compensation unit is used to compensate for the difference in phase adjustment of the coupling unit 402 on signals of different frequencies, so that the phase difference between the signal transmitted by the control signal unit and the signal transmitted by the signal amplification unit is maintained within a preset range when the power amplifier circuit amplifies signals of different frequencies. In this way, wideband phase shifting of the power amplifier circuit can be achieved.

[0156] For example, as shown in FIG. 7, one end of the phase compensation unit 601 is connected to the port 4c of the power divider 401, and the other end of the phase compensation unit 601 is connected to the input port 6a of the coupling unit 406.

[0157] The phase compensation unit 601 is used to adjust the phase of the signal B, so that the difference between the phase shift of the signal B and the difference value A is less than or equal to a preset value A, and the difference value A is the difference between the phase shift of the signal A at the coupling unit 402 and the phase shift of the signal A at the coupling unit 402 at a preset frequency. The preset value A can be 1 degree, 5 degrees or any value, which is not limited here.

[0158] In this way, the phase of the signal B can be adjusted by the phase compensation unit 601 to compensate for the difference in phase shift of the signal A at different frequencies at the coupling unit 402, so that the power amplifier circuit can support signal amplification at multiple frequencies, improve the application range of the power amplifier circuit, and improve the practicability.

[0159] In some embodiments, the phase compensation unit 601 can achieve fixed-degree phase shifting on the radio frequency signal at the center frequency, and the phase shifting angle will change linearly at other frequencies.

[0160] The fixed degree can be 90 degrees, 85 degrees or any value, which is not limited here. In this way, the phase shift variation rule of the coupling unit 402 on the radio frequency signal can be similar, so that the phase difference between the signal A and the signal B at each frequency is close to the phase difference between the signal A and the signal B at the center frequency.

[0161] In the embodiment of the present application, the phase compensation unit 601 can be a microstrip line (as shown in FIG. 8a).

[0162] The phase compensation unit 601 can also be a phase-shifting unit of a series inductance π-type network structure. For example, as shown in FIG. 8b, the phase-shifting unit of the series inductance π-type network structure includes a capacitor C11, a capacitor C12, and an inductor L11. A first end of the inductor L11 and a first end of the capacitor C11 are electrically connected and serve as an input end of the series inductance π-type network, a second end of the capacitor C11 is grounded, a second end of the inductor L11 and a first end of the capacitor C12 are electrically connected and serve as an output end of the series inductance π-type network, and a second end of the capacitor C12 is grounded.

[0163] The phase compensation unit 601 can also be a phase-shifting unit of a series capacitance π-type network structure. For example, as shown in FIG. 8c, the phase-shifting unit of the series capacitance π-type network structure includes a capacitor C11, an inductor L11, and an inductor L12. A first end of the capacitor C11 and a first end of the inductor L11 are electrically connected and serve as an input end of the series capacitance π-type network, a second end of the inductor L11 is grounded, a second end of the capacitor C11 and a first end of the inductor L12 are electrically connected and serve as an output end of the series capacitance π-type network, and a second end of the inductor L12 is grounded.

[0164] The phase compensation unit 601 can also be a phase-shifting unit of a series inductance T-type network structure. For example, as shown in FIG. 8d, the phase-shifting unit of the series inductance T-type network structure includes a capacitor C11, an inductor L11, and an inductor L12. A first end of the inductor L11 serves as an input end of the series inductance T-type network, a second end of the inductor L11, a first end of the inductor L12, and a first end of the capacitor C11 are electrically connected, a second end of the capacitor C11 is grounded, and a second end of the inductor L12 serves as an output end of the series inductance T-type network.

[0165] The phase compensation unit 601 can also be a phase-shifting unit of a series capacitance T-type network structure. For example, as shown in FIG. 8e, the phase-shifting unit of the series capacitance T-type network structure includes a capacitor C11, a capacitor C12, and an inductor L11. A first end of the capacitor C11 serves as an input end of the series capacitance T-type network, a second end of the capacitor C11, a first end of the capacitor C12, and a first end of the inductor L11 are electrically connected, a second end of the inductor L11 is grounded, and a second end of the capacitor C12 serves as an output end of the series capacitance T-type network.

[0166] The above-mentioned structures are only examples, and the phase compensation unit 601 can also be any type of structure (phase-shifting unit) having a phase adjustment function, which is not limited herein.

[0167] Exemplarily, taking the N77 signal as an example, the frequency range of the radio frequency signal is 3.3 GHz to 4.2 GHz, and the capacitance values of the capacitor C2 are 1.5 pF, 2 pF and 2.5 pF, FIG. 9 is a schematic view of the difference between the phase of the signal A output by the coupling unit 402 and the phase of the signal B input to the coupler 406.

[0168] As shown in FIG. 9, after the phase compensation unit is added, in the scenario where the capacitance C2 is 1.5 pF, the difference between the phase of the signal A output by the coupling unit 402 and the phase of the signal B input to the coupler 406 can be as shown in the curve 801 in FIG. 9; in the scenario where the capacitance C2 is 2 pF, the difference between the phase of the signal A output by the coupling unit 402 and the phase of the signal B input to the coupler 406 can be as shown in the curve 802 in FIG. 9; in the scenario where the capacitance C2 is 2.5 pF, the difference between the phase of the signal A output by the coupling unit 402 and the phase of the signal B input to the coupler 406 can be as shown in the curve 803 in FIG. 9; as can be seen from FIG. 9, in the scenario where the capacitance C1 is 1.5 pF, the phase difference between the signal A and the signal B under different frequencies is between 100 degrees and 105 degrees. In the scenario where the capacitance C1 is 2 pF, the phase difference between the signal A and the signal B is between 90 degrees and 100 degrees. In the scenario where the capacitance C1 is 2.5 pF, the phase difference between the signal A and the signal B is between 80 degrees and 85 degrees.

[0169] As can be seen from FIG. 9, the phase difference between the signal A and the signal B under each frequency is close to the phase difference between the signal A and the signal B under the center frequency, and the wideband phase shift of the power amplifier circuit can be realized.

[0170] In some embodiments, the phase compensation unit can further include two phase compensation modules, one of which is arranged between the coupling unit 406 and the power amplification unit 407, and the other of which is arranged between the coupling unit 406 and the power amplification unit 408. In this way, the phase of the signal b1 and the phase of the signal b2 can be adjusted, so as to maintain the phase difference between the signal transmitted by the control signal unit and the signal transmitted by the signal amplification unit within a preset range.

[0171] The structure of the phase compensation module is similar to that of the phase compensation unit 601 described above, and will not be described in detail here.

[0172] It can be understood that the above embodiments are described with the example that the control signal unit comprises the coupling unit 402 and the power amplification unit 403, and the signal amplification unit comprises the coupling unit 406, the power amplification unit 407, the power amplification unit 408 and the coupling unit 409. It can be understood that, in addition to the above power amplification units, the control signal unit can further comprise other functional units, for example, a voltage stabilizing unit for stabilizing voltage, a current limiting unit for limiting the current in the control signal unit to be less than a certain fixed value, etc.; the signal amplification unit can further comprise other functional units, for example, a voltage stabilizing unit for stabilizing voltage, a current limiting unit for limiting the current in the signal amplification unit to be less than a certain fixed value, etc.; which are not specifically limited here.

[0173] In addition, the power amplifier circuit of the load modulation structure can also be any other structure, for example, the signal amplification unit can comprise more or fewer power amplification units. The structure of the power amplifier circuit of the load modulation structure is not specifically limited here.

[0174] In the above embodiments shown in FIGS. 5 to 9, the power amplifier circuit divides the radio frequency signal into two signals through the power divider. The power amplifier circuit dividing the radio frequency signal into two signals through the coupler will be described below with reference to FIGS. 10 to 14.

[0175] For example, FIG. 10 is a structural schematic diagram of another power amplifier circuit provided by the embodiments of the present application. As shown in FIG. 10, the power amplifier comprises a coupling unit 902, a power amplification unit 903, a reactance unit 904, a coupling unit 905, a power amplification unit 906, a power amplification unit 907 and a coupling unit 908. The control signal unit can comprise the coupling unit 902, the power amplification unit 903 and the reactance unit 904; the signal amplification unit can comprise the coupling unit 902, the coupling unit 905, the power amplification unit 906, the power amplification unit 907 and the coupling unit 908.

[0176] The coupling unit 902 comprises an input port 8a, a coupling port 8b, a through port 8c and an isolation port 8d; the coupling unit 905 comprises an input port 9a, a coupling port 9b, a through port 9c and an isolation port 9d; and the coupling unit 908 comprises an input port 10a, a coupling port 10b, a through port 10c and an isolation port 10d.

[0177] As shown in FIG. 9, the input port 8a of the coupling unit 902 is used for inputting the radio frequency signal; the isolation port 8d of the coupling unit 902 is connected with the input end of the power amplification unit 903, and the output end of the power amplification unit 903 is connected with the isolation port 10d of the coupling unit 908; the through port 8c of the coupling unit 902 is connected with one end of the reactance unit 904, and the other end of the reactance unit 904 is grounded.

[0178] The coupling port 8b of the coupling unit 902 is connected with the input port 9a of the coupling unit 905; the coupling port 9b of the coupling unit 905 is connected with the input end of the power amplification unit 906, the output end of the power amplification unit 906 is connected with the through port 10c of the coupling unit 908; the through port 9c of the coupling unit 905 is connected with the input end of the power amplification unit 907, the output end of the power amplification unit 907 is connected with the isolation port 10d of the coupling unit 908; the input port 10a of the coupling unit 908 is used for outputting the amplified radio frequency signal, and the isolation port 9d of the coupling unit 905 is grounded.

[0179] In the embodiment of the application, the coupling unit 902 is used for dividing the radio frequency signal into two paths to obtain signal A and signal B. The power of the signal A and the signal B can be the same or different, which is not limited here.

[0180] The coupling unit 902 is also used for adjusting the phase of the signal A under the control of the reactance unit 904. The difference between the phase of the signal A and the phase of the radio frequency signal is related to the reactance of the reactance unit 404.

[0181] The power amplification unit 903 is used for power amplifying the signal A.

[0182] The reactance unit 904 is used for adjusting the reactance of the through port 5c, so that the difference between the phase of the signal A and the phase of the radio frequency signal changes, and the phase of the signal A changes.

[0183] The structure of the reactance unit 904 can refer to the structure of the reactance unit 404 described above, which will not be described in detail here.

[0184] The coupling unit 905 is used for decomposing the signal B into signal b1 and signal b2. The signal b1 and the signal b2 are orthogonal. Orthogonal can be understood as the phase difference between the signal b1 and the signal b2 being 90 degrees.

[0185] The power amplification unit 906 is used for signal amplifying the signal b1; the power amplifier 306 is used for signal amplifying the signal b2.

[0186] The coupling unit 908 is used for combining the amplified signal b1 and the amplified signal b2 to obtain the amplified radio frequency signal. The phase of the amplified signal b1 is affected by the impedance between the power amplification unit 906 and the coupling unit 908. The impedance is affected by the phase and amplitude of the amplified signal A transmitted by the isolation port 10d.

[0187] The structures and functions of the power amplification unit 903, the coupling unit 905, the power amplification unit 906, the power amplification unit 907 and the coupling unit 908 can refer to the related descriptions of the corresponding devices in FIG. 5, and will not be described in detail here.

[0188] The working principle and efficiency of the power amplifier circuit shown in FIG. 10 will be described below. The working principle is as follows:

[0189] When the input power of the radio frequency signal is small, the power of the signal A output by the coupling unit 402 is insufficient to turn on the transistor in the power amplification unit 903, the isolation port 10d of the coupling unit 908 presents an open circuit state, and the control signal unit does not perform load modulation on the signal amplification unit.

[0190] At this time, the power amplification unit 906 and the power amplification unit 907 respectively amplify the signal b1 and the signal b2. Since the power of the signal b1 and the signal b2 is low, and the power amplification unit 906 and the power amplification unit 907 both work in the linear region, the efficiency of the power amplification unit 906 and the power amplification unit 907 is low, and the efficiency of the power amplifier circuit is low.

[0191] As the input power gradually increases, the power of the signal A and the power of the signal B gradually increase, the efficiency of the power amplification unit 906 and the power amplification unit 907 gradually increases, and the efficiency of the power amplifier circuit gradually increases.

[0192] When the power of the radio frequency signal reaches the power A, the power of the signal A triggers the power amplification unit 903 to start working, and the amplified signal A is transmitted to the isolation port 10d of the coupling unit 908. The amplified signal A, the amplified signal b1 and the amplified signal b2 are superimposed, so that the output power of the power amplifier circuit is improved.

[0193] In addition, when the input power of the radio frequency signal reaches the power A, the control signal unit starts to perform load modulation on the signal amplification unit. It can also be understood that the amplified signal A starts to modulate the impedance of the through port 10c of the coupling unit 908 and the impedance at the coupling port 7b of the coupling unit 908. As the input power of the radio frequency signal increases, the power of the amplified signal A gradually increases, so that the load impedance of the power amplification unit 906 and the load impedance of the power amplification unit 907 gradually decrease, and the efficiency of the power amplification unit 407 and the efficiency of the power amplification unit 408 can still maintain a high level, and the efficiency of the power amplifier circuit as a whole for power amplification can still maintain a high level.

[0194] When the input power of the radio frequency signal reaches power B, the power amplification units 903, 906 and 907 all reach saturation, the output power of the power amplifier circuit reaches the maximum. And the load impedance of the power amplification units 906 and 907 is matched with the source impedance to reach the best, the efficiency of the power amplifier circuit reaches the maximum.

[0195] It can be understood that the load impedance of the signal amplification unit in the power amplifier circuit provided by the embodiment of the application is related to the amplitude and phase of the signal transmitted by the control signal unit. And the amplitude and phase of the signal are related to the phase shift and insertion loss of the coupling unit 902. Therefore, the debugging difficulty of the power amplifier circuit shown in FIG. 10 is related to the change of the phase shift and the change of the insertion loss of the coupling unit 902.

[0196] The change of the phase shift and the change of the insertion loss of the coupling unit 902 of each signal will be described below in combination with FIG. 11.

[0197] For example, taking the radio frequency signal as the N77 signal with the frequency range of 3.3GHz to 4.2GHz, and the capacitance values of the capacitor C4 as 1.5pF, 1.8pF and 2.2pF, FIG. 11 is a schematic diagram of the change of the phase shift of the signal A in the coupling unit 902 and the change of the insertion loss of the signal A transmitted in the coupling unit 902 when the capacitance C4 changes, provided by the embodiment of the application.

[0198] As shown in FIG. 11, in the scenario of the capacitance C4 being 1.5pF, the change of the phase shift of the signal A in the coupling unit 902 can be as shown in the curve 1001 in a of FIG. 11; in the scenario of the capacitance C4 being 1.8pF, the change of the phase shift of the signal A in the coupling unit 902 can be as shown in the curve 1002 in a of FIG. 11; in the scenario of the capacitance C4 being 2.2pF, the change of the phase shift of the signal A transmitted in the coupling unit 902 can be as shown in the curve 1003 in a of FIG. 11.

[0199] In the scenario of the capacitance C4 being 1.5pF, the change of the insertion loss of the signal A transmitted in the coupling unit 902 can be as shown in the curve 1004 in b of FIG. 11; in the scenario of the capacitance C4 being 1.8pF, the change of the insertion loss of the signal A transmitted in the coupling unit 902 can be as shown in the curve 1005 in b of FIG. 11. In the scenario of the capacitance C4 being 2.2pF, the change of the insertion loss of the signal A transmitted in the coupling unit 902 can be as shown in the curve 1006 in b of FIG. 11.

[0200] As can be seen from FIG. 11, if the capacitance value of C4 is adjusted from 1.5 pF to 1.8 pF, the phase shift of signal A transmitted by the coupling unit 902 changes between 5 degrees and 15 degrees, and the loss of signal A transmitted by the coupling unit 902 changes between 0 dB and 0.02 dB, with a small change. If the capacitance value of C4 is adjusted from 1.8 pF to 2.2 pF, the phase shift of signal A transmitted by the coupling unit 902 changes between 5 degrees and 15 degrees, and the loss of signal A transmitted by the coupling unit 902 changes between 0 dB and 0.03 dB, with a small change.

[0201] In addition, in the case where C4 has the same capacitance value, the phase shift of signal A of different frequencies in the coupling unit 902 is different. In the case where C4 has the same capacitance value, the loss of signal A of different frequencies transmitted by the coupling unit 902 changes differently.

[0202] Therefore, the loss of signal A transmitted by the coupling unit 902 changes little before and after the adjustment of the capacitance value of C4.

[0203] In addition, the power amplifier circuit shown in FIG. 10 does not need a power divider, and signal decomposition into two signals is achieved by a coupling unit, which is small in size and is conducive to the miniaturization of equipment.

[0204] It should be noted that the size of the coupling unit is inversely proportional to the characteristic impedance of the coupling unit. The size of the power divider is inversely proportional to the characteristic impedance of the power divider. In the case where the characteristic impedances are the same, since the coupling unit can be a multi-layer structure, the coupling unit has a smaller projected area in the circuit than the power divider, and thus the power amplifier circuit occupies a smaller area on the printed circuit board, which is conducive to the miniaturization of electronic equipment.

[0205] Compared with the LMBA shown in FIG. 3, in the process of adjusting the phase of signal A, the insertion loss of the coupling unit 902 shown in FIG. 10 changes little, so that the amplitude of the amplified signal A changes little, and the phase control of signal A and the amplitude control of signal A can be decoupled. In this way, when the phase of signal A is controlled, the influence on the amplitude of signal A does not need to be considered, the change of the load impedance of the signal amplification unit is easy to predict, and the design difficulty of the power amplifier circuit is reduced. In addition, the insertion loss of the coupling unit 902 is small, and the power loss is small.

[0206] For example, FIG. 12 is a diagram illustrating the phase shift and insertion loss of the signal B in the coupling unit 902 according to an embodiment of the present application. As shown in FIG. 12, in the case where the capacitance C4 is 1.5 pF, the phase shift of the signal B in the coupling unit 902 can be as shown by the curve 1201 in FIG. 12a; in the case where the capacitance C4 is 1.8 pF, the phase shift of the signal B in the coupling unit 902 can be as shown by the curve 1202 in FIG. 12a; and in the case where the capacitance C4 is 2.2 pF, the phase shift of the signal B in the coupling unit 902 can be as shown by the curve 1203 in FIG. 12a.

[0207] In the case where the capacitance C4 is 1.5 pF, the loss of the signal B in the coupling unit 902 can be as shown by the curve 1204 in FIG. 12b; in the case where the capacitance C4 is 1.8 pF, the loss of the signal B in the coupling unit 902 can be as shown by the curve 1205 in FIG. 12b; and in the case where the capacitance C4 is 2.2 pF, the loss of the signal B in the coupling unit 902 can be as shown by the curve 1206 in FIG. 12b.

[0208] As can be seen from FIG. 12, when the capacitance of the capacitance C4 is adjusted from 1.5 pF to 1.8 pF, the phase shift of the signal B changes between 0 degree and 2 degrees, and the loss of the signal B in the coupling unit 902 changes between 0.03 dB and 0.05 dB, which is relatively small. When the capacitance of the capacitance C4 is adjusted from 1.8 pF to 2.2 pF, the phase shift of the signal B changes between 0 degree and 2 degrees, and the loss of the signal B in the coupling unit 902 changes between 0.03 dB and 0.05 dB, which is relatively small.

[0209] In addition, in the case where the capacitance C4 has the same capacitance value, the phase shifts of the signal B of different frequencies in the coupling unit 902 are different. In the case where the capacitance C4 has the same capacitance value, the losses of the signal B of different frequencies in the coupling unit 902 are different.

[0210] On the basis of the above-described embodiment shown in FIG. 10, the power amplifier circuit according to an embodiment of the present application further includes a phase compensation unit. The phase compensation unit is located between the 8b and the input port 9a of the coupling unit 905. The phase compensation unit is configured to compensate for the difference in the phase adjustment of the coupling unit 902 to signals of different frequencies, so that the phase difference between the signal transmitted by the control signal unit and the signal transmitted by the signal amplification unit is maintained within a preset range when the power amplifier circuit amplifies signals of different frequencies. In this way, the wideband phase shift of the power amplifier circuit can be achieved.

[0211] For example, as shown in FIG. 13, one end of the phase compensation unit 1101 is connected to the coupling port 8b of the coupling unit 902, and the other end of the phase compensation unit 1101 is connected to the input port 9a of the coupling unit 905.

[0212] The phase compensation unit 1101 is configured to adjust the phase of the signal B.

[0213] In some embodiments, the phase compensation unit 1101 can be configured to make the difference between the phase shift of the signal B and the difference value B less than or equal to a preset value B, where the difference value B is the difference between the phase shift of the signal A at the coupling unit 902 and the phase shift of the signal A at the coupling unit 902 at a preset frequency. The phase shift of the signal A at the coupling unit 902 can be understood as the difference between the phase of the signal A output by the coupling unit 902 and the phase of the radio frequency signal input into the coupling unit 902; the phase shift of the signal A at the coupling unit 902 at a preset frequency can be understood as the difference between the phase of the signal A at a preset frequency output by the coupling unit 902 and the phase of the radio frequency signal at a preset frequency input into the coupling unit 902.

[0214] The preset value B can be 1 degree, 5 degrees or any value, which is not limited herein.

[0215] In this way, the phase compensation unit 1101 can adjust the phase of the signal B to compensate for the difference in phase shift of the signal A at different frequencies at the coupling unit 902, so that the power amplifier circuit can support signal amplification at multiple frequencies, improve the application range of the power amplifier circuit, and improve the practicability.

[0216] In other embodiments, the phase compensation unit 1101 can be configured to make the difference between the phase shift of the signal B and the difference value C less than or equal to a preset value B. The difference value C is the difference between the difference value B and the difference value D, and the difference value D is the difference between the phase shift of the signal B at the coupling unit 902 and the phase shift of the signal B at the coupling unit 902 at a preset frequency.

[0217] The phase shift of the signal B at the coupling unit 902 can be understood as the difference between the phase of the signal B output by the coupling unit 902 and the phase of the radio frequency signal input into the coupling unit 902; the phase shift of the signal B at the coupling unit 902 at a preset frequency can be understood as the difference between the phase of the signal B at a preset frequency output by the coupling unit 902 and the phase of the radio frequency signal at a preset frequency input into the coupling unit 902.

[0218] It can be understood that the phase difference between the input port and the coupling port of the coupling unit 902 will also be different at different frequencies. Therefore, the phase shift of the signal B by the phase compensation unit is also related to the phase shift of the signal B at the coupling unit 902.

[0219] In the embodiments shown in FIGS. 10-13, the through port 8c of the coupling unit 902 is connected to the reactance unit 904; and the coupling port 8b of the coupling unit 902 is connected to the coupling unit 905.

[0220] In some embodiments, the pass-through port 8c of the coupling unit 902 can also be connected with the coupling unit 905; the coupling port 8b of the coupling unit 902 is connected with the reactance unit 904. No specific limitation is made herein.

[0221] In the embodiments of the present application, the communication device can be understood as a device with a communication function. The device includes the power amplifier circuit provided in the embodiments of the present application to realize the signal amplification function. The communication device can include the electronic device, the base station, the radar, and the like. No specific limitation is made herein.

[0222] For example, FIG. 14 is a structural schematic diagram of an electronic device provided in the embodiments of the present application. As shown in FIG. 14, the electronic device includes a processor 110, an external memory interface 120, an internal memory 121, a universal serial bus (USB) interface 130, a charging management module 140, a power management module 141, a battery 142, an antenna 1, an antenna 2, a mobile communication module 150, a wireless communication module 160, an audio module 170, a loudspeaker 170A, a receiver 170B, a microphone 170C, a headset interface 170D, a sensor module 180, a key 190, a motor 191, an indicator 192, a camera 193, a display screen 194, and a subscriber identification module (SIM) card interface 195, and the like. The sensor module 180 can include a pressure sensor 180A, a gyroscope sensor 180B, a barometric pressure sensor 180C, a magnetic sensor 180D, an acceleration sensor 180E, a distance sensor 180F, a proximity light sensor 180G, a fingerprint sensor 180H, a temperature sensor 180J, a touch sensor 180K, an ambient light sensor 180L, a bone conduction sensor 180M, and the like.

[0223] It can be understood that the structure shown in the embodiments of the present application does not constitute a specific limitation on the electronic device. In other embodiments of the present application, the electronic device can include more or fewer components than shown, or combine certain components, or split certain components, or different arrangement of components. The components shown can be implemented in hardware, software, or a combination of software and hardware.

[0224] The wireless communication function of the electronic device can be realized through the antenna 1, the antenna 2, the mobile communication module 150, the wireless communication module 160, a modem processor, and the like.

[0225] The antennas 1 and 2 are used for transmitting and receiving electromagnetic wave signals. Each antenna in the electronic device can be used to cover a single or multiple communication frequency bands. Different antennas can also be multiplexed to improve the utilization of the antennas. For example, the antenna 1 can be multiplexed as a diversity antenna of a wireless local area network. In some other embodiments, the antennas can be used in combination with a tuning switch.

[0226] The mobile communication module 150 can provide a solution for wireless communication including 2G / 3G / 4G / 5G, etc. applied to the electronic device. The wireless communication module 160 can provide a solution for wireless communication including wireless local area networks (WLAN) (such as wireless fidelity (Wi-Fi) network), Bluetooth (BT), global navigation satellite system (GNSS), frequency modulation (FM), near field communication (NFC), infrared (IR) technology, etc. applied to the electronic device. In some embodiments, the antenna 1 of the electronic device is coupled with the mobile communication module 150, and the antenna 2 is coupled with the wireless communication module 160, so that the electronic device can communicate with the network and other devices through the wireless communication technology.

[0227] For example, as shown in FIG. 15a, the mobile communication module 150 can include a baseband chip 31, a radio frequency integrated circuit (RFIC) 32, and a power amplifier circuit 33.

[0228] The baseband chip 31 is used to convert data from the processor 110 into a baseband signal, including modulating and demodulating, digital filtering, equalization processing, etc. of the baseband signal. The RFIC 32 is used to convert the baseband signal from the baseband chip 31 into a radio frequency signal, which is transmitted through the power amplifier circuit 33 and the antenna 34. It should be noted that the baseband chip 31 and the RFIC 32 can also be integrated with the processor 110 in the SoC.

[0229] The power amplifier circuit 33 provided by the embodiments of the present application can improve the efficiency of power amplification when power backoff occurs. The power amplifier circuit 33 can be as shown in FIGS. 5 to 13 described above.

[0230] As shown in FIG. 15b, the wireless communication module 160 can include a baseband chip 41, a radio frequency integrated circuit (RFIC) 42, and a power amplifier circuit 43.

[0231] The baseband chip 41 is configured to convert data from the processor 110 into a baseband signal, including modulating and demodulating, digital filtering, equalization processing, etc. of the baseband signal. The RFIC 42 is configured to convert the baseband signal from the baseband chip 41 into a radio frequency signal, which is transmitted through the power amplifier circuit 43 and the antenna 44. It should be noted that the baseband chip 41 and the RFIC 42 can also be integrated with the processor 110 in a SoC.

[0232] The power amplifier circuit 43 provided by the embodiments of the present application can improve the efficiency of power amplification when power backoff occurs. The power amplifier circuit 43 can be as shown in FIGS. 5-13.

[0233] It should be noted that the module names involved in the embodiments of the present application can be defined as other names, as long as the functions of the modules can be realized, and the names of the modules are not limited specifically.

[0234] It should be noted that the user information (including but not limited to user equipment information, user personal information, etc.) and data (including but not limited to data for analysis, stored data, displayed data, etc.) involved in the embodiments of the present application are all information and data authorized by the user or authorized by all parties, and the collection, use and processing of the related data need to comply with the relevant laws, regulations and standards of the relevant countries and regions, and provide corresponding operation portal for the user to choose authorization or refusal.

[0235] The above detailed description of the embodiments of the present application further describes the purposes, technical solutions and beneficial effects of the present application. It should be understood that the above is only a specific embodiment of the present application, and is not used to limit the protection scope of the present application. Any modification, equivalent replacement, improvement, etc. made on the basis of the technical solutions of the present application should be included in the protection scope of the present application.

Claims

1. A power amplifier circuit, characterized by comprising: The power amplifier circuit comprises: a power divider, a first coupling unit, a first reactance unit, a first power amplifier unit and a signal amplifier unit; the power divider comprises a first port, a second port and a third port; the first coupling unit comprises a first input port, a first isolation port, a fourth port and a fifth port; the first port is configured to input a radio frequency signal, the second port is connected with the first input port, the first isolation port is connected with an input end of the first power amplifier unit, an output end of the first power amplifier unit is connected with a control end of the signal amplifier unit; the fourth port is connected with one end of the first reactance unit, the other end of the first reactance unit is grounded; and the fifth port is grounded; the third port is connected with an input end of the signal amplifier unit, and an output end of the signal amplifier unit is configured to output an amplified radio frequency signal; the power divider is configured to decompose the radio frequency signal into a first signal and a second signal at the first port; wherein the second port is configured to output the first signal, and the third port is configured to output the second signal; the first coupling unit is further configured to adjust a phase of the first signal; wherein a phase shift of the first signal at the first coupling unit is related to a reactance at the fourth port; the first reactance unit is configured to adjust the reactance at the fourth port; the first power amplifier unit is configured to amplify the first signal; the signal amplifier unit is configured to amplify the second signal; wherein a load impedance of the signal amplifier unit is negatively related to an input power of the radio frequency signal under control of the first signal input to the control end when power backoff occurs.

2. The power amplifier circuit of claim 1, wherein The first reactance unit comprises a first capacitor.

3. The power amplifier circuit of claim 1, wherein The power amplifier circuit further comprises a second reactance unit, one end of the second reactance unit is connected with the fifth port, and the other end of the second reactance unit is grounded; the second reactance unit is configured to adjust a reactance at the fifth port to reduce an insertion loss of the first coupling unit.

4. The power amplifier circuit of claim 3, wherein, A difference between a reactance value of the first reactance unit and a reactance value of the second reactance unit is less than a preset threshold value.

5. The power amplifier circuit of claim 4, wherein, The first reactance unit comprises a first capacitor, the second reactance unit comprises a second capacitor, and a difference between a capacitance value of the first capacitor and a capacitance value of the second capacitor is less than the preset threshold value.

6. The power amplifier circuit of claim 1, wherein, The power amplifier circuit further comprises a phase compensation unit between the power divider and the signal amplifier unit; the phase compensation unit is configured to adjust a phase of the second signal, so that an absolute value of a difference between a first phase difference and a second phase difference is less than or equal to a first threshold value; the first phase difference is a difference between a phase of the first signal at the first port and a phase of the second signal at the other end of the phase compensation unit when the radio frequency signal is at a first frequency; the second phase difference is a difference between the phase of the first signal at the first port and the phase of the second signal at the other end of the phase compensation unit when the radio frequency signal is at a second frequency.

7. The power amplifier circuit according to any one of claims 1 to 6, characterized by The signal amplification unit comprises a second coupling unit, a second power amplification unit, a third power amplification unit and a third coupling unit. The second coupling unit comprises a second input port, a second isolation port, a sixth port and a seventh port. The third coupling unit comprises a third input port, a third isolation port, an eighth port and a ninth port. The second input port is an input terminal of the signal amplification unit, the second isolation port is grounded, the sixth port is connected with an input terminal of the second power amplification unit, and an output terminal of the second power amplification unit is connected with the eighth port. The seventh port is connected with an input terminal of the third power amplification unit, an output terminal of the third power amplification unit is connected with the ninth port, and the third isolation port is a control terminal of the signal amplification unit. The third input port is used for outputting an amplified radio frequency signal. The second coupling unit is used for decomposing the second signal into a third signal and a fourth signal. The second power amplification unit is used for amplifying the third signal. The third power amplification unit is used for amplifying the fourth signal.

8. A power amplifier circuit, characterized by comprising: The third coupling unit is used for merging the third signal and the fourth signal under the control of the first signal to obtain the amplified radio frequency signal. Comprise: A first coupling unit, a first reactance unit, a first power amplification unit and a signal amplification unit. The first coupling unit comprises a first input port, a first isolation port, a fourth port and a fifth port. The first input port is used for inputting a radio frequency signal, the first isolation port is connected with an input terminal of the first power amplification unit, and an output terminal of the first power amplification unit is connected with a control terminal of the signal amplification unit. The fourth port is connected with one end of the first reactance unit, and the other end of the first reactance unit is grounded. The fifth port is connected with an input terminal of the signal amplification unit, and an output terminal of the signal amplification unit is used for outputting an amplified radio frequency signal. The first coupling unit is used for decomposing the radio frequency signal into a first signal and a second signal at the first input port; wherein the first isolation port is used for outputting the first signal, and the fifth port is used for outputting the second signal. The first signal is related to reactance at the fourth port in phase shift of the first coupling unit; The first reactance unit is used for adjusting the reactance at the fourth port; The first power amplification unit is used for amplifying the first signal; The signal amplification unit is used for amplifying the second signal; 9. The power amplifier circuit of claim 8, wherein, A load impedance of the signal amplification unit is negatively related to input power of the radio frequency signal in power backoff under control of the first signal inputting the control terminal.

10. The power amplifier circuit according to claim 8 or 9, characterized in that, The first reactance unit comprises a first capacitor. The power amplifier circuit further comprises a phase compensation unit between the first coupling unit and the signal amplification unit. The phase compensation unit is used for adjusting a phase of the second signal, so that an absolute value of a difference between a first phase difference and a second phase difference is less than or equal to a first threshold value. The first phase difference is a difference between a phase of the first signal at the first port and a phase of the second signal at the other end of the phase compensation unit when the radio frequency signal is at a first frequency. The second phase difference is a difference between the phase of the first signal at the first port and the phase of the second signal at the other end of the phase compensation unit when the radio frequency signal is at a second frequency.

11. A communications module, characterized by The radio frequency integrated circuit comprises: The radio frequency integrated circuit is configured to output a radio frequency signal. The power amplifier circuit is configured to amplify the radio frequency signal. The communication module comprises:

12. A communication device, characterized by The communication module is configured to output the amplified radio frequency signal to the antenna. The antenna is configured to transmit the amplified radio frequency signal. ​ ​

Images