Laminated assembly and vehicle

Abstract

The invention relates to a laminated assembly and a vehicle. The laminated assembly comprises a dielectric substrate; the metal ground is arranged on one surface of the dielectric substrate, and a slot line is formed in the metal ground to form an equivalent surface wave emitter; the feed structure is arranged on the surface wave emitter, and the feed structure is used for accessing a feed signal to excite the surface wave emitter to transmit a TM0 mode surface wave signal of a preset frequency band; the surface impedance modulation layer is arranged on the other side of the dielectric substrate, the surface impedance modulation layer is used for modulating surface wave signals, and the projection of the surface impedance modulation layer on the metal ground is located in the area where the metal ground is located; therefore, the included angle between the main radiation direction of the electromagnetic wave signal of the laminated component and the dielectric substrate is a non-zero preset angle, communication direction selection is realized, and the communication requirement in the application scene of the laminated component is met. When applied to obliquely mounted glass such as front windshields and rear windshields, the electromagnetic waves radiated in the horizontal direction are supported.

Description

Technical Field

[0001] The present application relates to the field of communication technology, and in particular to a laminated component and a vehicle. Background Art

[0002] Traditional vehicle-mounted glass antenna designs are mostly limited to low-frequency broadcast antennas on the rear window and omnidirectional antennas on the horizontal sunroof glass or small vertical side window triangular glass.

[0003] Traditional in-vehicle glass communication solutions are limited to the use of antennas on the front and rear windshields, which is very unfavorable for the multi-communication needs under the development trend of intelligent connected vehicles. Summary of the Invention

[0004] Based on this, it is necessary to provide a laminated component and a vehicle that can adapt to dielectric substrates of various tilt angles, so as to improve the flexibility of achieving high-quality communication based on the dielectric substrate.

[0005] In a first aspect, a laminated assembly is provided, comprising:

[0006] dielectric substrate;

[0007] A metal ground is provided on one side of the dielectric substrate, and a groove line is provided on the metal ground to form an equivalent surface wave launcher;

[0008] A feeding structure is provided on the surface wave transmitter, and is used to receive a feeding signal to stimulate the surface wave transmitter to transmit a TM0 mode surface wave signal of a preset frequency band;

[0009] A surface impedance modulation layer is provided on the other side of the dielectric substrate. The surface impedance modulation layer is used to modulate the surface wave signal. The projection of the surface impedance modulation layer on the metal ground is located within the area where the metal ground is located, so that the angle between the main radiation direction of the electromagnetic wave signal of the stacked component and the dielectric substrate is a non-zero preset angle.

[0010] In one embodiment, the size of the slot line matches half the wavelength, where the wavelength is the wavelength corresponding to the preset frequency band.

[0011] In one embodiment, the slot line has a first portion and a second portion intersecting each other, the second portion is in a rod shape; the first portion forms a surface wave launcher, and the feeding structure includes the second portion.

[0012] In one embodiment, the feeding structure is a coplanar waveguide structure.

[0013] In one embodiment, the surface impedance modulation layer includes a plurality of periodically arranged artificial high impedance units, and the artificial high impedance units are rectangular, circular, polygonal, diamond or elliptical structures.

[0014] In one embodiment, the metal ground matches the shape of the surface impedance modulation layer, and the metal ground is fan-shaped, triangular, or rectangular, and / or the surface impedance modulation layer is fan-shaped, triangular, or rectangular.

[0015] In one embodiment, when the metal ground is in a sector shape, the slot line is disposed close to the center of the sector shape.

[0016] In one embodiment, when the metal ground is fan-shaped, the fan-shaped curvature of the surface impedance modulation layer is smaller than or equal to the fan-shaped curvature of the metal ground.

[0017] In one embodiment, the metal ground, the slot line, the feeding structure and the surface impedance modulation layer are all mirror-symmetrical structures.

[0018] In one embodiment, the feeding structure receives the feeding signal through a coaxial cable.

[0019] In one embodiment, the edge of the dielectric substrate has a black edge region, and the metal ground and the surface impedance modulation layer are disposed in the black edge region.

[0020] In one embodiment, when the metal ground is fan-shaped, the center of the metal ground is located close to the edge of the dielectric substrate.

[0021] In one embodiment, the stacked assembly further comprises:

[0022] A surface wave suppression structure is provided on a dielectric substrate, and a first projection of the surface wave suppression structure on the dielectric substrate is distributed around a second projection to suppress the transmission of surface wave signals in non-TM0 modes on the dielectric substrate. The second projection is a projection of a metal ground on the dielectric substrate.

[0023] In one embodiment, the surface wave suppression structure includes a plurality of open-ended resonators, and the size of the open-ended resonators matches half the wavelength, which is the wavelength corresponding to the preset frequency band.

[0024] In one embodiment, the double-ended open-ended resonator is an axisymmetric structure, and an extension line of a symmetry center line of the double-ended open-ended resonator points toward the surface wave launcher.

[0025] In one embodiment, the opening direction of the double-ended open-circuit resonator faces away from the surface wave launcher.

[0026] In one embodiment, the open-ended resonator is a U-shaped, V-shaped or semicircular structure.

[0027] In one embodiment, the surface wave suppression structure is multi-layered, and the multi-layer surface wave suppression structures are respectively arranged on different surfaces of a dielectric substrate, or the multi-layer surface wave suppression structures are respectively arranged on different dielectric substrates;

[0028] Projections of surface wave suppression structures of different layers on a dielectric substrate overlap.

[0029] In one embodiment, the edge of the dielectric substrate has a black edge region, and the surface wave suppression structure is disposed in the black edge region.

[0030] In one embodiment, the dielectric substrate includes at least one layer of glass.

[0031] In one embodiment, when the glass is multi-layered, the metal ground and the feeding structure are both disposed on the outermost side of the multi-layered glass.

[0032] In a second aspect, a means of transport is provided, comprising:

[0033] body;

[0034] The above-mentioned laminated components are correspondingly mounted on the vehicle body; the dielectric substrate is the front windshield, the rear windshield or the sunroof glass.

[0035] The above-mentioned laminated assembly and vehicle have at least the following beneficial effects:

[0036] A metal ground is provided on a dielectric substrate, and slots are formed within the metal ground to form a surface wave transmitter. When excited by a feed signal from a feed structure, the surface wave transmitter generates a TM0 mode surface wave signal in a preset frequency band, which propagates along the metal ground. A surface impedance modulation layer is provided on the other side of the dielectric substrate, and its projection onto the metal ground is located within the area where the metal ground resides. Therefore, some of the TM0 mode surface waves generated by the surface wave transmitter remain unmodulated by the surface impedance modulation layer. The superimposed modulated surface waves affect the overall electromagnetic wave pattern, ensuring that the angle between the main radiation direction of the electromagnetic wave signal and the dielectric substrate is a non-zero preset angle. This enables communication direction selection and meets the communication requirements of stacked component applications. For example, when used in a vehicle, the device can support horizontal electromagnetic wave radiation on a front windshield, rear windshield, or sunroof glass with an angled edge, facilitating horizontal omnidirectional communication. BRIEF DESCRIPTION OF THE DRAWINGS

[0037] In order to more clearly illustrate the embodiments of the present application or the technical solutions in the conventional technology, the following briefly introduces the drawings required for use in the embodiments or the conventional technology descriptions. Obviously, the drawings described below are only some embodiments of the present application. For ordinary technicians in this field, other drawings can be obtained based on these drawings without creative work.

[0038] Figure 1 A perspective view of the structure of a stacked assembly in one or more embodiments;

[0039] Figure 2 A second front view of a dielectric substrate of a stacked assembly in one or more embodiments;

[0040] Figure 3 A structural diagram of a surface wave launcher in one or more embodiments;

[0041] Figure 4 A first elevation view of a dielectric substrate of a stacked assembly according to one or more embodiments;

[0042] Figure 5 Schematic diagram comparing the impact of different values of the arc β of the sector-shaped surface impedance modulation layer on the antenna pattern;

[0043] Figure 6 A schematic diagram comparing the impact of different values of the arc α of the sector-shaped metal ground on the antenna pattern;

[0044] Figure 7 Schematic diagram of the electric field intensity of TM0 surface waves excited in glass by a surface wave launcher in one or more embodiments;

[0045] Figure 8 FIG1 is a schematic diagram of electric field distribution when the radius of the metal ground takes different values in one embodiment;

[0046] Figure 9 1 is a directional pattern when the radius of the metal ground takes different values in one embodiment;

[0047] Figure 10 A schematic diagram of a surface wave launcher etched on a dielectric substrate at an angle of 40° to the horizontal ground in one or more embodiments;

[0048] Figure 11 is a schematic diagram of the layer structure of a stacked assembly in one or more embodiments;

[0049] Figure 12 To increase the far-field pattern at 5.915 GHz before and after the surface wave suppression structure, Figure 12 (a) is the directional diagram of the YOZ plane with Phi = 0°, Figure 12 (b) is the directional diagram of the Theta = 90°XOY plane;

[0050] Figure 13 is the reflection coefficient S of the stacked assembly in one or more embodiments 11 Schematic diagram of simulation results;

[0051] Figure 14 A schematic structural diagram of a stacked assembly in one embodiment;

[0052] Figure 15Schematic diagram of the structure of the stacked assembly in other embodiments;

[0053] Figure 16 A schematic structural diagram of a stacked assembly in another embodiment;

[0054] Figure 17 A schematic diagram of the relationship between the communication working state and the horizontal position of the stacked component;

[0055] Figure 18 Schematic diagram of the electric field intensity distribution of the dielectric substrate in the preset frequency band of 5.915 GHz after loading the surface impedance modulation layer;

[0056] Figure 19 Schematic diagram of the electric field intensity distribution on the dielectric substrate for the stacked component at the preset frequency band of 5.915 GHz, where: Figure 19 (a) is the distribution diagram without surface wave suppression structure. Figure 19 (b) is the distribution diagram with the surface wave suppression structure added;

[0057] Figure 20 is the far-field pattern of the stacked component at 5.915 GHz, where: Figure 20 (a) is the vertical plane Phi = 0°, that is, the direction diagram of the YOZ plane, Figure 20 (b) is the horizontal plane with Theta = 90°, i.e. the XOY plane directivity diagram;

[0058] Figure 21 It is the far-field horizontal plane radiation pattern (Theta=90°, XOY plane) at 5.915GHz when applied at three glass tilt angles of 30°, 40°, and 50°. DETAILED DESCRIPTION

[0059] To facilitate understanding of the present application, the present application will be described more fully below with reference to the accompanying drawings. The accompanying drawings provide embodiments of the present application. However, the present application may be implemented in many different forms and is not limited to the embodiments described herein. Rather, these embodiments are provided to make the disclosure of the present application more thorough and comprehensive.

[0060] Unless otherwise defined, all technical and scientific terms used herein have the same meaning as those commonly understood by those skilled in the art to which this application pertains. The terms used herein in the specification of this application are for the purpose of describing specific embodiments only and are not intended to limit this application.

[0061] It will be understood that the terms "first," "second," etc., used herein may be used to describe various elements, but these elements are not limited by these terms. These terms are only used to distinguish a first element from another element. For example, a first resistor may be referred to as a second resistor, and similarly, a second resistor may be referred to as a first resistor without departing from the scope of this application. The first resistor and the second resistor are both resistors, but they are not the same resistor.

[0062] It is understood that "at least one" means one or more, and "a plurality" means two or more. When used herein, the singular forms "a", "an", and "the" may also include the plural forms, unless the context clearly indicates otherwise. It should also be understood that the terms "include / comprise" or "have" and the like specify the presence of the stated features, wholes, steps, operations, components, parts, or combinations thereof, but do not exclude the possibility of the presence or addition of one or more other features, wholes, steps, operations, components, parts, or combinations thereof. At the same time, the term "and / or" used in this specification includes any and all combinations of the relevant listed items.

[0063] With the rapid development of science and technology, intelligent connected vehicles are gradually moving from science fiction to reality, becoming a new trend in the automotive industry. By integrating next-generation information and communications technologies, artificial intelligence, big data, and sensor technologies, intelligent connected vehicles enable intelligent information exchange and sharing between vehicles, roads, people, and the cloud. These vehicles possess capabilities such as complex environmental perception, intelligent decision-making, and collaborative control, providing users with a safe, convenient, and comfortable travel experience.

[0064] Communications technology is a cornerstone of intelligent connected vehicle (ICV) core technologies, supporting real-time communication and data exchange and a prerequisite for features like autonomous driving and remote driving. Ensuring stable and efficient communications in complex road conditions is a key challenge. Traditional external antennas are subject to space limitations and environmental interference, compromising communication quality. Therefore, in-vehicle glass antennas have emerged to optimize communication performance.

[0065] Automotive glass antennas cleverly integrate antenna functionality into the glass manufacturing process. However, traditional automotive glass antenna designs are limited to low-frequency broadcast antennas on the rear window and omnidirectional antennas on horizontal sunroof glass or small vertical side window triangles. This is because the surface wave phenomenon generated by high-frequency electromagnetic signals in glass with high dielectric constants and large dimensions significantly degrades antenna performance. Therefore, in high-frequency bands such as 5G and V2X (Vehicle to Everything), it is difficult to adapt to tilted front and rear windshield layouts while maintaining horizontal forward wide-angle coverage.

[0066] How to design antennas with efficient horizontal wide-angle coverage for inclined glass surfaces is crucial to promoting the development of in-vehicle communication technology.

[0067] Based on this, a laminated component is provided in the embodiment of the present application, such as Figure 1-Figure 2 As shown, it includes: a dielectric substrate 101, a metal ground 103, a feeding structure, and a surface impedance modulation layer 104.

[0068] A metal ground plane 103 is provided on one side of a dielectric substrate 101 and is slotted to form an equivalent surface wave transmitter 102. A feeding structure is provided on the surface wave transmitter 102 and is used to receive a feeding signal to excite the surface wave transmitter 102 to transmit a TM0 mode surface wave signal within a predetermined frequency band. A surface impedance modulation layer 104 is provided on the other side of the dielectric substrate and is used to modulate the surface wave signal. The projection of the surface impedance modulation layer 104 on the metal ground plane 103 is located within the region where the metal ground plane 103 is located, so that the angle between the main radiation direction of the electromagnetic wave signal of the stacked component and the dielectric substrate 101 is a non-zero predetermined angle.

[0069] The dielectric substrate 101 has a certain dielectric constant, providing a medium for the propagation of the electromagnetic field. The dielectric substrate 101 can be a transparent substrate, which is a substrate that is light-transmissive and provides a certain degree of support. For example, the transparent substrate can be, but is not limited to, a glass plate or a polycarbonate (PC) board.

[0070] Surface waves are electromagnetic waves that propagate along the interface between a dielectric and a conductor. Their electric and magnetic field components are primarily distributed near the interface, and their energy decays exponentially with perpendicular distance. Common surface wave modes include the TM (transverse magnetic) mode and the TE (transverse electric) mode. In the TM mode, the electric field has a longitudinal component, while the magnetic field is completely transverse. In the TE mode, the magnetic field has a longitudinal component, while the electric field is completely transverse.

[0071] After the metal ground 103 is grooved, the presence of the groove line destroys the continuity of the metal surface, resulting in a tangential component in the electric field at the groove line. The change in the electric field distribution at the groove line causes a corresponding change in the magnetic field distribution. The magnetic field forms a specific circulation pattern around the groove line, which couples with the electric field to form an electromagnetic field environment capable of exciting surface waves. At this time, the surface wave transmitter 102 formed by the groove line is equivalent to an excitation source, injecting electromagnetic energy into the interface between the dielectric substrate and air (or other external medium), exciting surface waves, which propagate along the interface, realizing the excitation of surface wave signals in the TM0 mode.

[0072] The geometric parameters of the slot line, such as its length and width, will affect its resonant characteristics. When the frequency of the incoming feed signal matches the resonant frequency of the slot line, a resonance phenomenon will form in the slot line. In the resonant state, the electromagnetic field energy in the slot line will be significantly enhanced, allowing more energy to be used to excite surface waves. Therefore, in the stacked component provided in the embodiment of the present application, the geometric parameters of the slot line can be designed according to the preset frequency band that needs to be supported. Optionally, the extension direction of the slot line is perpendicular or inclined to the propagation direction of the surface wave signal to be excited.

[0073] Specifically, a surface wave transmitter 102 is formed by providing a metal ground 103 on a dielectric substrate 101 and providing a slot line within the metal ground 103. The slot line acts as an equivalent magnetic dipole signal source. When stimulated by a feed signal supplied by the feed structure, it effectively excites surface waves in the TM0 mode within the grounded dielectric substrate 101, which propagate as cylindrical waves along the metal ground 103. A surface impedance modulation layer 104 is provided on the other side of the dielectric substrate, with its projection onto the metal ground located within the region of the metal ground 103. TM0 mode surface waves propagating along the dielectric substrate 101 within the region of the metal ground 103 are converted into leakage waves, which radiate away from the glass dielectric surface. The resulting superposition of these modulated surface waves influences the overall electromagnetic wave pattern, ensuring that the angle between the main radiation direction of the electromagnetic wave signal and the dielectric substrate 101 is a non-zero predetermined angle. This enables communication direction selection and meets the communication requirements of stacked component applications.

[0074] In one embodiment, the preset frequency band may be determined based on communication requirements. For example, in a vehicle-to-vehicle communication scenario, the preset frequency band may be the V2X frequency band. The frequency band primarily used by V2X is the 5.9 GHz band. Alternatively, the preset frequency band may be at least one of the high, low, mid, and ultra-high frequency bands.

[0075] In one embodiment, the size of the slot line matches half the wavelength, which is the wavelength corresponding to the preset frequency band. g / 2(λ g The excited electric field can be effectively coupled to the main mode electric field of the grounded dielectric substrate 101, thereby effectively exciting the surface wave, reducing energy loss in other forms, such as radiation loss and ohmic loss, thereby improving the excitation efficiency of the surface wave, obtaining a stronger surface wave with less input energy, and reducing power consumption under the same surface wave intensity excitation.

[0076] In one embodiment, Figure 3As shown, the slotline 107 has a first portion 1071 and a second portion 1072 intersecting each other, with the second portion 1072 being rod-shaped. The first portion 1071 forms a surface wave launcher, and the feed structure 106 includes the second portion 1072. The rod-shaped shape of the second portion 1072 can be understood as meaning that the shape of the second portion 1072 is approximately rod-shaped and does not necessarily require to be linear.

[0077] In one embodiment, the first portion 1071 of the groove line 107 is an annular groove with an opening. The annular groove can be rectangular, circular, or elliptical. The annular groove communicates with the rod-shaped groove of the second portion 1072 to form a T-shaped or racket-shaped groove line 107.

[0078] When there is only one rod-shaped slot, the rod-shaped slot is connected to the annular slot at the opening of the annular slot to form a T-shaped slot line 107. The structure is simple, the layout on the surface of the metal ground 103 is convenient, and it is easy to integrate with other circuit elements or structures, which is conducive to improving the integration and performance. The vertical part of the T-shaped slot line 107 can be used as the main excitation channel (for feeding), so that the electromagnetic wave energy is more effectively injected into the slot line 107, and the horizontal part ( Figure 3 The coupling area with the surrounding electromagnetic field can be increased, thereby enhancing the excitation effect of the surface wave and improving the field strength and propagation efficiency of the surface wave.

[0079] Among them, Figure 2-Figure 3 As shown, when there are multiple rod-shaped slots, the multiple rod-shaped slots are connected to the corresponding annular slots at the opening of the annular slot to form a racket-shaped slot line. The head area of the racket-shaped slot line is large, which can provide a larger capacitance and inductance effect, and form an impedance matching relationship with the main part of the slot line (the part other than the head), which helps to broaden the working frequency band of the surface wave, so that the surface wave transmitter 102 can effectively excite and transmit the surface wave in a wider frequency range, thereby improving the bandwidth performance of the stacked component.

[0080] Furthermore, when a racket-shaped slot line has multiple rod-shaped slots, the multiple rod-shaped slots can be viewed as a multi-stage impedance matching network. By adjusting the geometric parameters of each slot (such as length, width, and spacing), they can be independently adjusted to form an equivalent distributed parameter circuit (such as inductance and capacitance). By gradually adjusting the parameters of each slot, a smooth impedance transition can be achieved, reducing reflections and achieving efficient matching over a wider frequency band.

[0081] In one embodiment, Figure 3As shown, the feeding structure 106 is a coplanar waveguide structure. The coplanar waveguide (CPW) structure and the metal ground 103 can be arranged in the same plane, forming a highly efficient surface wave launcher 102 design. This design eliminates the need for multi-layer structures or complex wiring, occupies a small space, and, compared to traditional microstrip line feeding methods, helps reduce the thickness of stacked components, improves the level of integration, and simplifies the manufacturing process. Furthermore, the coplanar waveguide structure, when used for feeding, exhibits low loss and minimal radiation leakage, enabling more efficient transmission of the feed signal to the surface wave launcher, reducing energy loss during signal transmission and improving feeding efficiency. This, in turn, enhances the overall performance of the surface wave launcher 102 and ensures efficient excitation and transmission of surface waves.

[0082] When the dielectric substrate 101 includes glass and a coplanar waveguide structure is adopted, the antenna is a planar structure and can achieve feeding without metal vias, so that the glass antenna fully adopts a multi-layer planar coupling structure design without a metallized via structure, does not destroy the integrity of the glass, and meets the requirements of vehicle-mounted glass antennas in terms of process and strength.

[0083] like Figure 3 As shown, by reusing the metal ground 103 as part of the coplanar waveguide structure and the second portion 1072 of the slot line 107 as part of the coplanar waveguide structure (for example, taking the second portion 1072 as a rod-shaped slot as an example, in this case, the coplanar waveguide structure includes the rod-shaped slot and the metal grounds on both sides of the rod-shaped slot), a coplanar design of the coplanar waveguide structure, the metal ground 103, and the surface wave launcher 102 can be achieved. This is beneficial for improving the design compactness of the antenna structure and reducing the occupied area on the dielectric substrate while achieving matching. It is further beneficial for integration in the black border area at the edge.

[0084] In one embodiment, the surface impedance modulation layer 104 includes a plurality of periodically arranged artificial high impedance units. Since the surface wave of the TM0 mode propagates in the form of cylindrical waves, in order to achieve stable radiation in the azimuth plane and to achieve tilt angle control in the pitch plane, it is necessary to maintain modulation uniformity. Therefore, a metal unit with periodic size changes is provided on a radial path with the surface wave transmitter as the center, so that the antenna can achieve leakage wave radiation in a wider azimuth plane. According to the sinusoidal modulation principle, according to the material properties of the dielectric substrate, the stacking layout and the target radiation angle requirements, the spacing of the metal units and the physical size of the metal units can be reasonably controlled, so as to realize the conversion of surface wave propagation into space waves for radiation. The artificial high impedance unit is rectangular (such as Figure 1 and Figure 4 as shown), circular, polygonal, diamond or elliptical structures.

[0085] The sizes of the multiple artificial high impedance units in each cycle may be different. For example, in an optional embodiment, Figure 4 As shown, the size of the artificial high-impedance unit can be increased and then decreased along the direction of surface wave propagation from the position of the surface wave transmitter 102. This initial increase and subsequent decrease in the size of the artificial high-impedance unit allows the impedance modulation of the surface wave to exhibit a gradual change. As the size of the artificial high-impedance unit gradually increases, the energy of the surface wave is gradually guided and concentrated, helping to enhance the energy intensity of the surface wave in the early stages of propagation, reduce premature energy dissipation into the surrounding space, and ensure that the surface wave can stably propagate over long distances in the desired direction. When the size of the artificial high-impedance unit begins to decrease, the accumulated surface wave energy is gradually released, smoothly transitioning to a state more conducive to conversion to space waves. This avoids drastic energy changes at the moment of conversion, which can lead to problems such as uneven radiation. This achieves smooth regulation of surface wave energy from propagation to conversion, optimizing the entire propagation and conversion process.

[0086] In addition, along the position of the surface wave transmitter 102 toward the propagation direction of the surface wave, the size of the artificial high-impedance unit can be first increased and then decreased, which can more accurately control the radiation angle. Through the different modulation effects of artificial high-impedance units of different sizes on the surface wave, more flexible and detailed control of the radiation angle of the pitch plane can be achieved, meeting the requirements for the radiation direction in different application scenarios, thereby facilitating the realization of radiation control in the horizontal direction.

[0087] The artificial high-impedance unit can be formed by patching, printing, or other methods. It is understood that based on the principle of holographic interference, in order to achieve communication application requirements in different scenarios, such as horizontal wide-angle coverage, horizontal narrow-beam high-gain coverage, or multi-beam applications, there are different requirements for adjusting the surface wave characteristics. Therefore, the artificial high-impedance unit used in the surface impedance modulation layer 104 can be a rectangular, circular, polygonal, triangular, diamond, elliptical, or other sub-wavelength shaped metal unit.

[0088] Circular artificial high-impedance units, due to their symmetry, are insensitive to the polarization of electromagnetic waves, making them suitable for scenarios requiring omnidirectional radiation or wide-angle coverage. Furthermore, rounded edges reduce edge scattering and, at high frequencies, lower parasitic radiation losses from surface waves. Polygonal artificial high-impedance units can also be used in scenarios with horizontal wide-angle coverage.

[0089] Optionally, in one embodiment, Figure 4As shown, the artificial high-impedance unit is a rectangular metal unit. The rectangular shape is simple and regular, and its parameters, such as size and side length ratio, are easy to determine and adjust, facilitating precise control. When using patching or printing methods, the rectangular metal unit has clear edges and a relatively simple manufacturing process, ensuring high manufacturing precision and consistency, facilitating large-scale production. Furthermore, the rectangular metal unit can effectively modulate and control specific polarization waves, reducing signal polarization distortion and improving communication quality.

[0090] It should be noted that because TM0 surface waves can propagate in the grounded dielectric substrate 101, while TE0 mode surface waves cannot propagate, the propagation characteristics of TM0 mode surface waves along the surface of the dielectric substrate 101 are significantly affected by the shape of the metal ground 103 having metallic properties. Therefore, the shape of the metal ground 103 can be designed according to the surface wave propagation requirements.

[0091] In one embodiment, the metal ground 103 is fan-shaped (eg Figure 2 As shown), a triangle or a rectangle, and the outer contour of the surface impedance modulation layer 104 is adapted to the shape of the metal ground 103.

[0092] To achieve communication application requirements in different scenarios, such as horizontal wide-angle coverage, horizontal narrow-beam high-gain coverage, or multi-beam applications, different requirements are imposed on the adjustment of surface wave characteristics. The overall shape of the surface impedance modulation layer 104 and the metal ground 103 can also be rectangular, circular, or triangular. The specific structure of the metal ground 103 and the surface impedance modulation layer 104 is not limited in this application.

[0093] The relative position of the surface impedance modulation layer 104 and the metal ground 103 has a significant impact on the antenna performance:

[0094] When the surface impedance modulation layer 104 is fan-shaped, the arc angle α of the metal ground 103 remains unchanged at 0°, and the arc angles of the surface impedance modulation layer 104 region are set to β = 0°, 30°, and 45°, respectively. The cross-sectional results of the antenna elevation and azimuth radiation patterns at the frequency point of 5.915 GHz are as follows: Figure 5 See Figure 5It can be seen that the curvature β of the sector-shaped surface impedance modulation layer 104 has a certain influence on the forward and lateral radiation gains of the antenna. When β increases from 0° to 30°, the effect on the lateral radiation coverage of the antenna is small, but the forward radiation is concave and the gain decreases; when β increases from 30° to 45°, the lateral radiation gain of the antenna decreases significantly, resulting in a decrease in the radiation coverage, while the forward radiation concave disappears and the gain increases. This is mainly because as the area of the sector-shaped surface impedance modulation layer 104 decreases, the TM0 surface wave generated by the surface wave transmitter 102 contains some unmodulated electromagnetic waves, and the superimposed modulated TM0 surface wave has a significant impact on the overall antenna pattern. Therefore, the sector curvature of the surface impedance modulation layer 104 can be reasonably selected to obtain the main radiation in the desired direction. In the application scenarios of the front and rear windshields of the vehicle, the curvature of the sector-shaped surface impedance modulation layer 104 can be designed to be β = 30° based on the comprehensive coverage and forward gain performance.

[0095] Similarly, the change of the curvature of the metal ground 103 will also have a significant impact on the antenna radiation performance. The curvature of the surface impedance modulation layer 104 β = 30° remains unchanged. When the curvature of the metal ground 103 is set to α = 0°, 15° and 30° respectively, the cross-sectional results of the antenna elevation and azimuth radiation patterns at the 5.915GHz frequency are as follows: Figure 6 See Figure 6 It can be seen that the curvature of the sector-shaped metal ground 103 has a certain impact on the forward and lateral radiation gains of the antenna. When α is set to 0° and 15° respectively, the fluctuation of the antenna's lateral radiation coverage gain (±90°) slows down, and the coverage performance is better. When α is 30°, a pit appears in the lateral radiation, and the coverage performance deteriorates. In addition, the forward radiation gain gradually increases as the curvature of the metal ground 103 decreases. This is mainly because the metal ground 103 is a condition that supports the propagation of TM0 surface waves. When the sector curvature angle π-2α of the metal ground 103 decreases, that is, when α increases, the unmodulated TM0 surface wave mode will gradually disappear, resulting in a reduction in lateral radiation energy and an increase in forward radiation gain. Therefore, the sector curvature angle of the metal ground 103 can be reasonably selected according to the desired main radiation direction to obtain better radiation coverage performance. In the application scenarios of the front and rear windshields of vehicles, considering the coverage range and forward gain performance, the curvature of the metal ground 103 α can be set to 15°.

[0096] In one embodiment, the metal ground 103 and the surface impedance modulation layer 104 are both fan-shaped as an example for description:

[0097] like Figure 2 As shown, the radius R and radian angle (π-2α) of the metal ground 103 (the installation method may include printing, patch, etc.)

[0098] The surface wave transmitter 102 excites the electric field distribution of the TM0 surface wave in the grounded dielectric substrate 101. Figure 8 As shown, a test was conducted using glass as dielectric substrate 101. Metal ground 103 covered the entire dielectric substrate 101 to support the propagation of the TM0 surface wave mode. This cylindrical wave diffused outward in a nearly concentric circular pattern, filling the entire glass dielectric. However, considering the practical application of a vehicle-mounted windshield antenna, the antenna design must be located within the black border area of the window, and the metal ground 103 area should not be too large. To this end, the metal ground 103 and glass were designed in a fan-shaped shape. This maintains the concentric circular propagation characteristics of the TM0 surface wave within the confined space, adapting to the spatial constraints of the black border area of the vehicle window without interfering with the TM0 surface wave propagation mode (cylindrical wave morphology).

[0099] like Figure 8 As shown, the change of different fan radii will significantly affect the excited TM 0δ Surface wave electric field distribution. Specifically, taking the preset frequency band as the V2X band as an example, according to the wavelength of the surface wave in the glass medium at 5.915GHz, the fan radius is set to 30mm, 45mm, 65mm and 83mm respectively, and the corresponding surface wave modes are TM 01 ,TM 02 ,TM 03 and TM 04 . In TM 0δ In the pattern, “0” indicates that the magnetic field has no component in the propagation direction, and “δ” indicates the number of times the field strength has the maximum value along the propagation direction.

[0100] like Figure 9 As shown, TM 01 ,TM 02 ,TM 03 and TM 04 The radiation patterns of the four surface wave modes at 5.915 GHz are given in elevation and azimuth planes, respectively. The coordinate system is the same as Figure 10 The antenna is aligned with the horizontal plane, meaning it is positioned at a 40° angle relative to the horizontal plane. Research has shown that varying the radius R can cause variations in the waveform of the initial radiation pattern of the surface wave transmitter 102 antenna. Therefore, the structure of the metal ground plane 103 (such as its area and shape) has a significant impact on the propagation characteristics of the TM0 surface wave. Those skilled in the art can adjust the shape of the metal ground plane 103 to control the antenna's initial radiation waveform based on communication requirements.

[0101] In one embodiment, the radius of the metal ground 103 can be designed to be 83 mm. In this case, the corresponding surface wave mode is TM 04The metal ground 103 area provides a minimum surface impedance modulation layer 104, further enabling beam control while balancing the antenna's initial radiation gain and the black border width. When the laminated component is used for a vehicle's front or rear windshield, it can be beneficial for modulating the primary radiation direction horizontally, maximizing horizontal forward azimuth coverage.

[0102] In one embodiment, Figure 2 As shown, when the metal ground 103 is fan-shaped, the groove line is arranged close to the center of the fan-shaped circle.

[0103] Surface wave transmitter 102, acting as a signal source, can excite uniform electromagnetic waves in grounded dielectric substrate 101 and propagate them in the form of cylindrical waves. Placing surface wave transmitter 102 at the edge of metal ground 103 facilitates full utilization of the limited area of metal ground 103 for antenna radiation beam control. Designing the slot lines close to the center of symmetry ensures that the excited surface wave signals are uniformly and symmetrically distributed across the sector-shaped metal ground 103. Therefore, the laminated assembly provided in the embodiments of the present application, by placing the slot lines close to the center of the sector-shaped metal ground 103, ensures that antenna radiation beam control is performed within the limited area of metal ground 103 and that the excited surface wave signals are uniformly and symmetrically distributed across the metal ground 103.

[0104] In one embodiment, Figure 1 As shown, when the metal ground 103 is fan-shaped, the fan-shaped curvature of the surface impedance modulation layer 104 is less than or equal to the fan-shaped curvature of the metal ground 103 .

[0105] The surface impedance modulation layer 104 is based on the metal ground 103. Without the metal ground 103 below the surface impedance modulation layer 104, the modulation effect on the TM0 surface wave mode electromagnetic waves will be lost. Therefore, the fan-shaped curvature of the surface impedance modulation layer 104 needs to be less than or equal to the fan-shaped curvature of the metal ground 103.

[0106] In one embodiment, Figure 1 As shown, the metal ground 103 , the slot line, the feeding structure 106 and the surface impedance modulation layer 104 are all mirror-symmetrical structures.

[0107] Designing the metal ground 103 as a mirror-symmetrical structure ensures a stable and symmetrical electromagnetic field around the slot line, allowing surface waves to be excited and propagated according to the desired pattern. The feed structure 106 is responsible for feeding the excitation signal to the surface wave transmitter 102. During signal transmission, it needs to match the electromagnetic field environment created by the metal ground 103 and the slot line. The mirror-symmetrical structure ensures that the electromagnetic field generated by the feed signal during transmission is also symmetrically distributed, thereby reducing unevenness and distortion during signal transmission.

[0108] The mirror-symmetric structure of surface impedance modulation layer 104 allows it to work in conjunction with an existing symmetrical electromagnetic field environment to effectively modulate surface waves. Therefore, the mirror-symmetric design of the metal ground 103, slot lines, feed structure 106, and surface impedance modulation layer 104 ensures that all steps, from the excitation source of the surface wave to the modulation process during propagation, operate within a symmetrical electromagnetic environment, suppressing electromagnetic interference and improving signal communication quality.

[0109] In one embodiment, the feeding structure 106 receives a feeding signal via a coaxial cable 108 .

[0110] like Figure 3 As shown, when the feeding structure 106 adopts a coplanar waveguide structure, the slot lines of the coplanar waveguide structure are correspondingly connected to the slot lines of the surface wave launcher 102 to form an enclosed slot line structure. Figure 3 As shown, the enclosed slotted structure divides the metal ground 103 into a first conductor inside the slotted structure and a second conductor outside the slotted structure. The inner conductor of the coaxial cable 108 is connected to the first conductor on the inner side of the feeding structure 106 slotted, and the outer conductor of the coaxial cable 108 is connected to the second conductor on the outer side of the feeding structure 106 slotted. The core wire of the coaxial cable 108 can be connected to the first conductor and the second conductor by welding. In the embodiment of the present application, the feeding structure 106 is simplified by adopting a coaxial cable 108 to coplanar waveguide structure and a slotted connection at the feeding point. The cost is low and the processing is convenient, which significantly improves the product manufacturing efficiency and reduces the cost. In addition, when the laminated component is a vehicle-mounted glass, its production can also meet the antenna process requirements of the current vehicle-mounted glass, and the cost is similar to that of traditional vehicle-mounted glass, which is conducive to the integration and industrialization of RF front-end circuits and intelligent networked vehicle-mounted glass.

[0111] In one embodiment, the coaxial cable 108 may be directly welded and fed using a 50 ohm coaxial line, wherein the inner conductor and outer conductor of the 50 ohm coaxial line may be welded to both sides of the slot line.

[0112] In one embodiment, the edge of the dielectric substrate 101 has a black edge region, and the metal ground 103 and the surface impedance modulation layer 104 are disposed in the black edge region.

[0113] By arranging the metal ground 103 and the surface impedance modulation layer 104 in the black edge region, it is possible to avoid affecting the light transmission performance of the metal ground 103 and the surface impedance modulation layer 104 in the light transmission region.

[0114] In one embodiment, dielectric substrate 101 includes functional layers. By placing metal ground 103 and surface impedance modulation layer 104 in the black border region, the performance of the functional layers can be guaranteed. For example, when a functional layer such as a display film is provided in the light-transmitting region of dielectric substrate 101, placing metal ground 103 and surface impedance modulation layer 104 in the black border region can avoid occupying the display area of the display film layer, thereby providing a larger display window for the user.

[0115] For another example, when the dielectric substrate 101 includes other functional layers such as dimming and temperature control, by arranging the metal ground 103 and the surface impedance modulation layer 104 in the black edge area, a larger functional layer area can be provided for dimming and temperature control, providing users with better environmental parameters.

[0116] Other examples of arranging the metal ground 103 and the surface impedance modulation layer 104 under the black border area to ensure the performance of the functional layer are not listed here exhaustively.

[0117] In one embodiment, when the metal ground 103 is fan-shaped, the center of the metal ground 103 is positioned near the edge of the dielectric substrate 101. Positioning the center of the metal ground 103 near the edge allows the arc of the fan-shaped edge to extend toward the center of the dielectric substrate 101, enabling surface wave propagation on the dielectric substrate 101. By utilizing the surface wave propagation phenomenon and the superposition of surface wave signals in the TM0 mode excited by the surface wave transmitter 102, the main radiation direction of a preset frequency band is modulated, such that the main radiation direction forms an angle with the dielectric substrate 101, thereby achieving horizontal radiation on the tilted dielectric substrate 101.

[0118] In the area outside the metal ground 103, there is leakage of unwanted stray mode surface waves, such as TE0 mode surface waves, which affects the overall communication performance of the stacked component. Therefore, in one embodiment, Figure 1 As shown, the stacked assembly further includes a surface wave suppression structure 105 .

[0119] A surface wave suppression structure 105 is provided on the dielectric substrate 101, and a first projection of the surface wave suppression structure 105 on the dielectric substrate 101 is distributed around a second projection to suppress the transmission of surface wave signals in non-TM0 mode on the dielectric substrate 101. The second projection is the projection of the metal ground 103 on the dielectric substrate 101.

[0120] Specifically, by converting the surface waves of the TM0 mode propagating along the dielectric substrate 101 in the metal ground 103 area into leakage waves and radiating away from the surface of the glass dielectric, and then distributing the surface wave suppression structure 105 on the periphery of the vertical projection of the metal ground 103, the stray surface wave signals not modulated by the surface impedance modulation layer 104 are suppressed to reduce interference, thereby improving the radiation performance of the entire stacked component and thus enhancing the communication quality of the preset frequency band.

[0121] In one embodiment, Figure 2 and Figure 4 As shown, the surface wave suppression structure 105 includes a plurality of open-ended resonators, and the size of the open-ended resonators matches half the wavelength, which is the wavelength corresponding to the preset frequency band.

[0122] A double-ended open-circuit resonator is essentially a transmission line with both ends open. When its length is half a wavelength, a voltage antinode (current node) will form at the open end, and a current antinode (voltage node) will form at the center point, which will induce a strong localized electromagnetic field and significantly enhance the scattering and energy absorption of the double-ended open-circuit resonator on surface waves. The resonant frequency of the double-ended open-circuit resonator matches the frequency of the surface wave to be suppressed, so the impedance characteristics of the double-ended open-circuit resonator will greatly limit the propagation path of the surface wave, thereby suppressing its diffusion along the surface of the medium. In addition, because it is folded into a U-shaped structure, the currents excited by the surface wave on it are in opposite directions and cancel each other out, thus not generating secondary radiation.

[0123] In one embodiment, the open-ended resonator is an axisymmetric structure, and an extension line of a symmetry center line of the open-ended resonator points toward the surface wave launcher 102 .

[0124] The axisymmetric structure of the double-ended open-circuit resonator, combined with the notch structure, can facilitate the realization of a half-wavelength size design of a single structure in a smaller area, improve the compactness of the surface wave suppression structure 105, and facilitate the layout of the surface wave suppression structure 105 in a narrower black-border area.

[0125] In addition, the opening of the double-ended open-ended resonator can be facing outward or inward, but the extension of its symmetry center line must point to the surface wave transmitter 102. The spacing between adjacent double-ended open-ended resonators and the number of turns of the double-ended open-ended resonator can be set according to the surface wave intensity to be suppressed and the judgment.

[0126] When the extended line of the symmetric center line of the double-ended open-ended resonator points to the surface wave transmitter 102, the electromagnetic field distribution around it has good symmetry, so that the effect of the double-ended open-ended resonator on the surface wave signal remains consistent in all directions, and there will be no poor or unstable local suppression effect due to uneven field distribution, thereby ensuring the stability and reliability of surface wave suppression.

[0127] In addition, with the fan-shaped metal ground 103 design, the surface wave is distributed in a fan-shaped manner, and the extension line of the symmetry center line of the double-ended open-ended resonator points to the surface wave transmitter 102, which can ensure that the symmetry axis of the double-ended open-ended resonator is aligned with the propagation direction of the surface wave. At this time, the suppression effect of the double-ended open-ended resonator on the surface wave is effectively guaranteed due to phase matching.

[0128] In one embodiment, the open end of the open-ended resonator faces away from the surface wave launcher 102. When the open end faces away from the surface wave propagation direction, a strong impedance contrast is formed between the open end of the open-ended resonator (high impedance) and the surface wave propagation path (low impedance). This causes the surface wave energy to be reflected back to the source or radiated into free space through the open-ended resonator, rather than continuing to propagate along the dielectric surface. This enhances surface wave reflection and energy dissipation, thereby improving the surface wave suppression effect.

[0129] In one embodiment, the double-ended open-circuit resonator is U-shaped (e.g. Figure 2 as shown), V-shaped or semicircular structure.

[0130] The U-shaped double-ended open-circuit resonator increases the effective flow length of the current through the curved path, and the required physical size is smaller when achieving the same frequency resonance. For example, the total length of the U-shaped double-ended open-circuit resonator can be close to λ g / 2 (half the wavelength of the preset frequency band), but the actual occupied area is smaller, which is conducive to the compact design of high frequency bands.

[0131] By combining a dielectric substrate with a U-shaped half-wavelength double-ended open-ended resonator array, a surface wave suppression structure is formed, effectively reducing the adverse effects of unwanted surface wave leakage on antenna radiation. This simple design eliminates the need for metallized vias, maintains glass integrity, and facilitates large-scale production.

[0132] The V-shaped open-ended resonator has a flexible opening angle (e.g., 60° or 90°). By varying the angle, the resonant frequency and directional suppression effect of the open-ended resonator can be controlled. For example, a sharp V-angle provides greater suppression of obliquely incident surface waves.

[0133] The semicircular double-ended open-circuit resonator, with its symmetrical arc structure, has a uniform response to surface waves from different directions and is suitable for scenarios requiring omnidirectional suppression.

[0134] To better illustrate the beneficial effects of the laminated assembly provided in the embodiment of the present application, Figure 3 、 4 As shown, the surface wave signal leakage is suppressed by loading a U-shaped half-wavelength resonant unit array (forming a surface wave suppression structure 105) at an appropriate position outside the metal ground 103. The suppression effect is shown in FIG. Figure 19As shown in (b), it can be clearly seen that the surface wave electric field intensity in the non-grounded dielectric area (area not covered by the metal ground 103) in the dielectric substrate 101 is significantly weakened. Figure 12 As shown in FIG, the effect of adding the surface wave suppression structure 105 on the antenna pattern is given. Figure 12 (a) shows the YOZ section of the elevation plane at 5.915 GHz, that is, the directional pattern of the vertical plane, and Figure 12 (b) shows the XOY section of the azimuth plane at 5.915 GHz, i.e., the radiation pattern in the horizontal plane. The dotted line and the solid line represent the antenna performance before and after adding the surface wave suppression structure 105, respectively.

[0135] See also Figure 12 It can be found that when the metal ground 103 adopts a fan-shaped design, the propagation, reflection and diffraction superposition of the TM0 surface wave along the large-area dielectric substrate 101 are suppressed, and the stray effect is reduced.

[0136] In one embodiment, the surface wave suppression structure 105 is multi-layered, and the multi-layer surface wave suppression structures 105 are respectively disposed on different surfaces of the dielectric substrate 101 , and the projections of the surface wave suppression structures 105 of different layers on the dielectric substrate 101 overlap.

[0137] When the surface wave suppression structure 105 is a multilayer structure, for example, Figure 2 and Figure 4 When a double-layer structure (including the surface wave suppression structure 105 1051 and the surface wave suppression structure 105 1052) is formed, the projections of the surface wave suppression structure 105 in a direction perpendicular to the surface of the dielectric substrate 101 overlap with each other, which can ensure the capacitance (capacitance) between the two metal layers, improve the surface wave suppression effect, and help reduce the area of the single-layer surface wave suppression structure 105, thereby facilitating the design of the surface wave suppression structure 105 in the black edge area of the dielectric substrate 101.

[0138] In one embodiment, the dielectric substrate 101 has a black border region at its edge, and the SAW suppression structure 105 is disposed in the black border region. Providing the SAW suppression structure 105 in the black border region can avoid affecting the light transmission performance of the SAW suppression structure 105 in the light-transmitting region.

[0139] In one embodiment, dielectric substrate 101 includes a functional layer (not shown). By placing surface acoustic wave suppression structure 105 in the black border region, the performance of the functional layer can be guaranteed. For example, when a functional layer such as a display film layer is disposed in the light-transmitting region of dielectric substrate 101, placing surface acoustic wave suppression structure 105 in the black border region can avoid occupying the display area of the display film layer, thereby providing a larger display window for the user.

[0140] For another example, when the dielectric substrate 101 includes other functional layers such as dimming and temperature control, by arranging the surface wave suppression structure 105 in the black edge area, a larger functional layer area can be provided for dimming and temperature control, providing users with better environmental parameters.

[0141] Other examples of arranging the surface wave suppression structure 105 under the black border area to ensure the performance of the functional layer are not exhaustively listed here.

[0142] In one embodiment, Figure 11 As shown, dielectric substrate 101 includes at least one layer of glass. Glass has a high dielectric constant, and high-frequency signals such as 5G or V2X experience significant surface wave transmission on the glass surface. The laminated assembly provided in the embodiments of the present application utilizes surface waves generated by electromagnetic waves in a high-dielectric-constant medium and surface wave signals in the TM0 mode excited by a surface wave transmitter to achieve antenna beamforming. This allows for the design of antenna radiation directions at a certain angle to the surface of dielectric substrate 101, meeting primary radiation communication requirements in a predetermined direction, such as the horizontal azimuth.

[0143] In addition, the laminated component provided in the embodiment of the present application further eliminates leaked surface wave signals and improves antenna radiation performance by disposing a surface wave suppression structure 105 on the periphery of the metal ground 103 .

[0144] In one embodiment, Figure 1 and Figure 11 As shown, in the case of multiple layers of glass, the metal ground 103 and feed structure 106 are both located on the outermost side of the glass. The outermost side of the glass refers to the side of the glass that is exposed to the atmosphere, rather than adjacent to other glass. When the laminated assembly is installed in a vehicle, the outermost side of the glass can be the side away from ambient light. Placing the metal ground 103 and feed structure 106 on the outermost side of the glass facilitates external feed routing, eliminating the need for opening holes in the glass and ensuring the stability of the glass structure.

[0145] For example, Figure 11 As shown, taking double-layer glass as an example, in which at least one layer of glass includes a first glass plate and a second glass plate, the metal ground 103 and the feeding structure 106 are both disposed on the surface of the first glass member 1011 away from the second glass plate. This facilitates feeding power on the outside of the first glass member 1011 without requiring a hole to be drilled in the glass.

[0146] In one embodiment, the glass is a vehicle-mounted glass. The first surface of a first glass element 1011 faces the first surface of a second glass element 1012, while the second surface of the first glass element 1011 is spaced away from the second glass element 1012. Accordingly, the second surface of the second glass element 1012 is spaced away from the first glass element 1011. When the glass is installed on a vehicle body, when viewed from inside the vehicle, the following visible components are, in order: the second surface of the first glass element 1011, the first surface of the first glass element 1011, the first surface of the second glass element 1012, and the second surface of the second glass element 1012.

[0147] In one embodiment, Figure 11 As shown, dielectric substrate 101 further includes an intermediate layer 1013, which is positioned between first glass member 1011 and second glass member 1012. Intermediate layer 1013 can be made of an adhesive material such as PVB (Polyvinyl Butyral) or EVA (Ethylene Vinyl Acetate Copolymer). Through a lamination process, intermediate layer 1013 tightly bonds first glass member 1011 and second glass member 1012 to form a sandwich structure. This significantly enhances the overall strength and toughness of the glass while also significantly improving its impact resistance and safety performance.

[0148] Based on this description, the surface wave launcher 102 and the metal ground 103 are both disposed on the second surface of the first glass member 1011 , and the surface impedance modulation layer 104 is disposed on the first surface of the first glass member 1011 .

[0149] Of course, in other embodiments, the surface wave launcher 102, metal ground 103, and surface impedance modulation layer 104 may have other layer arrangements. For example, the surface wave launcher 102 and metal ground 103 may be arranged on the first surface of the second glass member 1012, and the surface impedance modulation layer 104 may be arranged on the second surface of the second glass member 1012. In this case, the connection point between the coplanar waveguide structure and the coaxial cable 108 may be located near the edge of the glass, so that a feed line can be introduced at the edge of the glass, i.e., side feeding can be enabled. Alternatively, the surface wave launcher 102 and metal ground 103 may be arranged on the second surface of the second glass member 1012, and the surface impedance modulation layer 104 may be arranged on the first surface of the second glass member 1012, so that feeding can be facilitated from the outside of the second glass member 1012.

[0150] For another example, the surface wave launcher 102 and the metal ground 103 can be arranged on the first surface of the first glass member 1011, and the surface impedance modulation layer 104 can be arranged on the second surface of the first glass member 1011. In this case, the surface wave launcher 102 and the metal ground 103 are in the interlayer, and the point where the coplanar waveguide structure is connected to the coaxial cable 108 can be set close to the edge of the glass so that a feeding line can be introduced at the edge of the glass, that is, feeding can be performed from the side.

[0151] In one embodiment, the surface wave launcher 102, the metal ground 103, the surface impedance modulation layer 104, and the surface wave suppression structure 105 can be disposed correspondingly in the black edge areas on the first and second surfaces of the first glass member 1011 to avoid negative impacts on the light transmission performance of the transparent area of the glass.

[0152] In one embodiment, a vehicle is provided, comprising: a vehicle body and the aforementioned laminated assembly, the laminated assembly being mounted on the vehicle body. The dielectric substrate 101 in the laminated assembly is a front windshield, a rear windshield, or a sunroof. At least a portion of such glass has a certain angle with the horizontal ground. This angle varies depending on the vehicle model and is not specifically limited in this application.

[0153] In one embodiment, when the dielectric substrate 101 is a front windshield, after adopting the sector-shaped metal ground 103, the maximum gain (GainMax) of the vehicle glass in the forward direction +Y (directly in front of the vehicle) is increased to 2dBi. At the same time, the 10dB horizontal beam width is increased to more than 180°, the coverage capability of the vehicle's front field of view is greatly enhanced, and the radiation in different directions is more uniform. In addition, compared Figure 12 The results of (a) and 12 (b) show that after adding the surface wave suppression structure 105, the gain curve of the stacked component becomes smoother and the fluctuation is significantly reduced, ensuring the stability of the gain fluctuation.

[0154] Furthermore, the present application adds a surface impedance modulation layer 104 (such as Figure 1 and Figure 4 As shown in FIG, the size and periodic distribution of the artificial high-impedance units of the surface impedance modulation layer 104 can be designed for a specific preset frequency band and desired radiation angle (corresponding to the main radiation direction). This fully utilizes the TM0 surface wave signals propagating on the metal ground 103 and effectively converts them into electromagnetic waves that radiate primarily in the horizontal direction, thereby improving the antenna's horizontal coverage performance.

[0155] When the dielectric substrate 101 is a skylight glass and the edge of the skylight glass has an inclination angle, the metal ground 103, the surface wave launcher 102 and the surface impedance modulation layer 104 can also be set at the edge of the skylight glass, for example, the black edge area of the skylight glass. In this case, based on the description in the above embodiment, horizontal radiation can still be maintained.

[0156] To better illustrate the implementation process of the transportation provided in the embodiment of the present application, an example is given below:

[0157] The metal ground 103 and the surface impedance modulation layer 104 are both fan-shaped. The surface wave launcher 102 is used to excite the TM 04 mode surface wave signal.

[0158] like Figure 4 The surface impedance modulation layer 104 on the dielectric substrate 101 is shown in FIG. 04 The modulated surface wave signal's beam is steered to achieve wide-angle radiation coverage in the horizontal azimuth plane toward the vehicle's exterior. The surface impedance modulation layer 104 is located within the vertical projection of the sector-shaped metal ground plane 103, and together they form a holographic antenna structure. This structure, designed based on the principles of holographic modulation and the required target inclination angle, consists of periodically arranged rectangular metal patch units of specific dimensions. The sector-shaped surface impedance modulation layer 104 has a radian angle of (π-2β), ensuring flexible and accurate beam steering.

[0159] To further suppress unnecessary surface wave signal leakage, refer to Figure 1 、 Figure 2 and Figure 4 A surface wave suppression structure 105 is added to the periphery of the fan-shaped projection area corresponding to the metal ground 103. The surface wave suppression structure 105 can be composed of a half-wavelength U-shaped metal unit array, which can effectively reduce the leakage interference of additional surface wave signals and optimize antenna performance.

[0160] Figure 13 The simulation results of the reflection coefficient S11 of the glass antenna described in Example 1 are presented. The results show that within the V2X operating frequency band, the reflection coefficient S11 is less than -14dB, indicating excellent impedance matching performance and excellent communication performance within this frequency band.

[0161] In other embodiments, the arc angle π-2α of the metal ground 103 and the arc angle π-2β of the surface impedance modulation layer 104 can be changed accordingly to meet different radiation coverage requirements, such as Figure 14-16 As shown, this is not an exhaustive list.

[0162] The laminated component provided in the embodiment of the present application is designed to address the growing demand for diversified applications in intelligent connected vehicles. It utilizes the surface wave propagation phenomenon of dielectric substrates such as glass to interact with the surface waves excited by holographic antennas. It can also support full forward vision capabilities on inclined vehicle glass such as front windshields / rear windshields, no longer limited by the shark fin on the roof or the space inside the vehicle. This solves the difficult problem of balancing the number and performance of antennas in intelligent connected vehicles and provides an efficient solution to communication needs in complex application scenarios.

[0163] The vehicle provided in the embodiment of the present application, by being equipped with the above-mentioned stacked components, cleverly utilizes the inevitable surface wave phenomenon of dielectric substrates such as glass in the high-frequency band, and supports electromagnetic waves radiated in the horizontal direction on tilted glass such as the front windshield and the rear windshield, which is conducive to achieving omnidirectional communication in the horizontal direction.

[0164] In addition, the dimensions of the related structures of the above-mentioned stacked components can be adjusted according to requirements to adapt to receiving and transmitting devices of wireless communication systems with different frequency bands.

[0165] exist Figure 17 , the relative position of the vehicle glass of Example 1 and the horizontal plane is shown: the angle between the glass and the horizontal plane is 40°.

[0166] exist Figure 18 , the electric field intensity distribution on the second surface of the first glass member 1011 of the glass antenna is shown. The results show that the electric field intensity of the TM0 surface wave is significantly concentrated in the distribution area of the surface impedance modulation layer 104 under the control of the surface impedance modulation layer 104.

[0167] Furthermore, by comparing Figure 18 and Figure 19 It can be seen that the electric field intensity is significantly weakened in the non-metallic region of the glass medium, which indicates that more surface wave signals are effectively modulated by the surface impedance modulation layer 104 and successfully radiate outward from the glass surface.

[0168] Figure 20 The far-field radiation patterns of the glass antenna loaded with the surface impedance modulation layer 104 at the frequency of 5915 MHz in the elevation plane (vertical plane) (YOZ section) and the azimuth plane (horizontal plane) (XOY section) are presented. Figure 18 and Figure 12 By comparison, we can see that the maximum radiation tilt has been successfully adjusted to the horizontal forward direction (+Y direction). This adjustment significantly increases the maximum horizontal gain (GainMax), jumping from 2dBi in traditional technology to 6dBi. At the same time, the 10dB horizontal beamwidth is maintained within the ideal range of 180° in the forward direction.

[0169] In view of the differences in the angles between different vehicle models and the front and rear windshields and the horizontal plane, the embodiments of the present application take into account application scenarios where the angle between the windshield and the horizontal plane is in the range of 30° to 50°.

[0170] Figure 21The far-field azimuth plane (XOY plane) radiation pattern of the automotive glass at a frequency of 5.915 GHz is intuitively displayed at three angles of 30°, 40°, and 50° to the horizontal plane. It can be seen from the figure that the 10 dB horizontal plane wave width at angles of 30°, 40°, and 50° all stably reaches 180° and above, and the gain shows a stable linear growth trend. The laminated component provided in the embodiment of the present application can be applied to most vehicle models and has a wide range of applications.

[0171] Because the laminated assembly provided in this embodiment leverages the surface wave control and suppression capabilities of a high-dielectric-constant environment to achieve beam steering, it is particularly suitable for large-sized automotive glass. Furthermore, benefiting from the antenna's radiation tilt control characteristics, the laminated assembly provided in this embodiment can be used for both front and rear windshields, achieving full horizontal radiation coverage for both the front and rear fields of view, meeting the growing demands of intelligent in-vehicle communication applications.

[0172] In the description of this specification, reference to the terms "some embodiments" or "other embodiments" means that the specific features, structures, materials, or characteristics described in conjunction with the embodiment or example are included in at least one embodiment or example of the present application. In this specification, the schematic descriptions of the above terms do not necessarily refer to the same embodiment or example.

[0173] The technical features of the above-mentioned embodiments can be combined arbitrarily. In order to make the description concise, not all possible combinations of the technical features in the above-mentioned embodiments are described. However, as long as there is no contradiction in the combination of these technical features, they should be considered to be within the scope of this specification.

[0174] The above-described embodiments merely represent several implementation methods of the present application. While the descriptions are relatively specific and detailed, they should not be construed as limiting the scope of the present application. It should be noted that a person of ordinary skill in the art may make various modifications and improvements without departing from the spirit of the present application, and these modifications and improvements fall within the scope of protection of the present application. Therefore, the scope of protection of the present application shall be determined by the appended claims.

Claims

1. A laminated component, characterized in that: include: dielectric substrate; A metal ground is provided on one side of the dielectric substrate, and a groove line is provided on the metal ground to form an equivalent surface wave launcher; A feeding structure is provided on the surface wave transmitter, and the feeding structure is used to receive a feeding signal to stimulate the surface wave transmitter to transmit a TM0 mode surface wave signal of a preset frequency band; A surface impedance modulation layer is provided on the other surface of the dielectric substrate, the surface impedance modulation layer is used to modulate the surface wave signal, and the projection of the surface impedance modulation layer on the metal ground is located within the area where the metal ground is located, so that the angle between the main radiation direction of the electromagnetic wave signal of the stacked component and the dielectric substrate is a non-zero preset angle.

2. The stacked assembly according to claim 1, wherein: The size of the slot line matches half the wavelength, and the wavelength is the wavelength corresponding to the preset frequency band.

3. The stacked assembly according to claim 1, wherein: The slot line has a first portion and a second portion intersecting each other, and the second portion is in a rod shape; the first portion forms the surface wave launcher, and the feeding structure includes the second portion.

4. The stacked assembly according to claim 1, wherein: The feeding structure is a coplanar waveguide structure.

5. The stacked assembly according to claim 1, wherein: The surface impedance modulation layer includes a plurality of periodically arranged artificial high impedance units, and the artificial high impedance units are rectangular, circular, polygonal, diamond or elliptical structures.

6. The stacked assembly according to claim 1, wherein: The metal ground is fan-shaped, triangular or rectangular, and the outer contour of the surface impedance modulation layer is adapted to the shape of the metal ground.

7. The stacked assembly according to claim 6, wherein: When the metal ground is sector-shaped, the groove line is arranged close to the center of the sector.

8. The stacked assembly according to claim 6, wherein: When the metal ground is fan-shaped, the fan-shaped curvature of the surface impedance modulation layer is smaller than or equal to the fan-shaped curvature of the metal ground.

9. The stacked assembly according to any one of claims 1 to 8, characterized in that: The metal ground, the slot line, the feeding structure and the surface impedance modulation layer are all mirror-symmetrical structures.

10. The stacked assembly according to any one of claims 1 to 8, characterized in that: The feeding structure receives the feeding signal through a coaxial cable.

11. The stacked assembly according to any one of claims 1 to 8, characterized in that: The edge of the dielectric substrate has a black edge area, and the metal ground and the surface impedance modulation layer are arranged in the black edge area.

12. The stacked assembly according to any one of claims 1 to 8, characterized in that: When the metal ground is fan-shaped, the center of the metal ground is arranged close to the edge of the dielectric substrate.

13. The stacked assembly according to claim 1, wherein: The stacked assembly further comprises: A surface wave suppression structure is provided on the dielectric substrate, and a first projection of the surface wave suppression structure on the dielectric substrate is distributed around a second projection, so as to suppress the transmission of surface wave signals in a non-TM0 mode on the dielectric substrate. The second projection is a projection of the metal ground on the dielectric substrate.

14. The stacked assembly according to claim 13, wherein: The surface wave suppression structure includes a plurality of open-ended resonators, and the size of the open-ended resonators matches half a wavelength, where the wavelength is a wavelength corresponding to the preset frequency band.

15. The stacked assembly according to claim 14, wherein: The double-ended open-ended resonator is an axisymmetric structure, and an extension line of a symmetry center line of the double-ended open-ended resonator points to the surface wave launcher.

16. The stacked assembly according to claim 15, wherein: The opening direction of the double-ended open-ended resonator faces a direction away from the surface wave launcher.

17. The stacked assembly according to claim 14, wherein: The double-ended open-circuit resonator has a U-shaped, V-shaped or semicircular structure.

18. The stacked assembly according to claim 13, wherein: The surface wave suppression structure is multi-layered, and the multi-layer surface wave suppression structure is respectively arranged on different surfaces of the dielectric substrate, or the multi-layer surface wave suppression structure is respectively arranged on different dielectric substrates; Projections of the surface wave suppression structures of different layers on the dielectric substrate overlap.

19. The stacked assembly according to any one of claims 13 to 18, characterized in that The edge of the dielectric substrate has a black edge area, and the surface wave suppression structure is arranged in the black edge area.

20. The stacked assembly according to claim 1, wherein: The dielectric substrate includes at least one layer of glass.

21. The stacked assembly according to claim 20, wherein: In the case that the glass is multi-layered, the metal ground and the feeding structure are both arranged on the outermost sides of the multi-layered glass.

22. A means of transport, characterized in that: include: body; The laminated assembly according to any one of claims 1 to 21, wherein the laminated assembly is mounted on the vehicle body; The dielectric substrate is a front windshield, a rear windshield or a skylight glass.

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