Wireless power information simultaneous transmission device and method

Abstract

The invention discloses a wireless power information simultaneous transmission device and method. The wireless power information simultaneous transmission device comprises a direct-current stabilized power supply, a full-bridge inverter circuit, a semi-bridgeless active rectifying circuit, a magnetic coupling resonance network, a load, a signal receiving circuit, a current transformer, a signal transmitting circuit and the like. A phase-shift semi-bridgeless active rectifier circuit (S-BAR) is adopted on a secondary side of a traditional wireless power transmission system, and simultaneous transmission of high-frequency wireless power information is realized through hardware circuit design. Based on the device, the electric energy can be transmitted from the primary side to the secondary side without contact, and the information can be transmitted from the secondary side to the primary side at the same time. Compared with a traditional wired electric energy transmission device, the device does not depend on an entity wire any more, metal resource consumption and potential safety hazards are reduced, and the device is more convenient and flexible; compared with a traditional wireless power transmission device, the device can realize simultaneous transmission of power and information, and saves the cost required by an additional information transmission device.

Description

Technical Field

[0001] The present invention relates to the fields of power electronics technology, wireless power transmission technology and communication principle, and in particular to a wireless power information simultaneous transmission device and method. Background Art

[0002] After more than three hundred years of development, electricity, as a convenient and safe energy source, has become one of the most widely used energy sources in human society. Traditional electricity transmission and distribution methods rely on physical wires, but there are problems such as high metal resource consumption, safety hazards and shortened equipment life. To solve these challenges, people began to explore wireless power transmission technology. This emerging technology no longer requires physical wires, reduces metal resource consumption and safety hazards, and has been widely used in various fields. Wireless power transmission is changing the perception of energy transmission methods and providing modern society with more flexible and efficient solutions. This innovative technology brings a more sustainable and intelligent prospect for future energy transmission, driving society towards a more advanced and sustainable energy era.

[0003] In the process of wireless power transmission, from the primary side to the secondary side, the electric energy usually needs to exist in the form of alternating current. However, in actual applications, direct current is often required at the terminal load. Therefore, wireless power transmission technology is combined with inverter technology and rectification technology in most cases. The traditional rectification scheme, due to the use of diode devices, leads to large losses in the AC-DC conversion process. With the birth of a series of controllable devices such as MOSFET, synchronous rectification technology also emerged and was widely used.

[0004] In actual application scenarios, the control measures taken to ensure the stability and high efficiency of the wireless power transmission system generally require the acquisition of secondary side electrical parameters. However, due to the physical loss of connection in the wireless transmission system, contactless communication is required. Using radio frequency modules in the information field for wireless communication is a solution, but it has problems such as matching delay and adding communication modules. Another method is to use the energy transmission channel to inject information into the energy channel to achieve power information fusion control. Summary of the invention

[0005] Based on this, the present invention proposes a wireless power information simultaneous transmission device and method to achieve wireless power information simultaneous transmission of low-power electrical equipment.

[0006] To achieve the above object, the present invention provides a wireless power information simultaneous transmission device, which includes a DC regulated power supply, a full-bridge inverter circuit, a semi-bridgeless active rectifier circuit, a magnetic coupling resonant network, a load R L, signal receiving circuit, current transformer and signal sending circuit; the DC regulated power supply passes through the full-bridge inverter circuit and magnetic coupling resonant network in sequence; the semi-bridgeless active rectifier circuit and the load R L The signal receiving circuit is connected to the full-bridge inverter circuit; the current transformer is respectively connected to the semi-bridgeless active rectifier circuit and the signal sending circuit; the signal sending circuit is respectively connected to the current transformer and the second end of the fifth switch tube S5 and the second end of the sixth switch tube S6 in the semi-bridgeless active rectifier circuit;

[0007] The semi-bridgeless active rectifier circuit includes: a first diode D1, a second diode D2, a fifth switch tube S5, a sixth switch tube S6 and a fourth capacitor C L The cathode of the first diode D1 is connected to the cathode of the second diode D2 and the fourth capacitor C L One end and load R L The anode of the first diode D1 is connected to the first end of the fifth switch tube S5, and the third end of the fifth switch tube S5 is connected to the third end of the sixth switch tube S6 and the fourth capacitor C L The other end and the load R L The other end of the second diode D2 is connected to the first end of the sixth switch tube S6, and the anode of the first diode D1, the first end of the fifth switch tube S5, the anode D2 of the second diode and the first end of the sixth switch tube S6 are respectively connected to the magnetic coupling resonant network;

[0008] The signal receiving circuit comprises: a sampling resistor R, a differential circuit module, a low-pass filter and a high-pass filter, wherein the sampling resistor R is connected in series with a DC regulated power supply and a full-bridge inverter circuit on the primary side, and the primary side is one side of the full-bridge inverter circuit, i.e., the power transmitting end of the wireless transmission system; the two ends of the sampling resistor R are respectively connected to the positive and negative inputs of the differential circuit module, and the receiving signal is output through the low-pass filter and the high-pass filter;

[0009] The signal sending circuit comprises: a microcontroller MCU, an advanced phase shift module, a forward zero-crossing detection module, a forward integration module, a forward waveform correction module, a forward control signal generation module, a reverse zero-crossing detection module, a reverse integration module, a reverse waveform correction module, a reverse control signal generation module, a drive circuit module 1, a drive circuit module 2, a drive circuit module 3 and a drive circuit module 4;

[0010] The leading phase shift module includes: resistor R10, resistor R11, resistor R12, capacitor C5 and fourth operational amplifier AD8065; the forward zero-crossing detection module includes: resistor R13, resistor R14, resistor R15 and first comparator TLV3502; the forward integration module includes: resistor R16, capacitor C6, seventh MOSFET switch tube and fifth operational amplifier AD8066; the forward waveform correction circuit includes: resistor R17, resistor R18 and sixth operational amplifier AD8066; the forward control signal generation module includes: resistor R19, resistor R20, resistor R21 and second comparator TLV3502; the reverse zero-crossing detection module includes: resistor R22, resistor R23, resistor R24 and the third comparator TLV3502; the reverse integration module includes: resistor R25, capacitor C7, the eighth MOSFET switch tube and the seventh operational amplifier AD8066; the reverse waveform correction module includes: resistor R26, resistor R27 and the eighth operational amplifier AD8066; the reverse control signal generation module includes: resistor R28, resistor R29, resistor R30 and the fourth comparator TLV3502; the drive circuit module 1 and the drive circuit module 2 are the first drive chip UCC27524, and the drive circuit module 3 and the drive circuit module 4 are the second drive chip UCC27524; the microcontroller MCU is the main control chip STM32G431C8T6.

[0011] Specifically, the rated voltage of the DC regulated power supply is 30V.

[0012] Specifically, the operating frequencies of the full-bridge inverter circuit, the semi-bridgeless active rectifier circuit and the magnetic coupling resonant network all need to reach above 1 MHz.

[0013] Specifically, the semi-bridgeless active rectification circuit can realize high-frequency synchronous rectification at the operating frequency.

[0014] Furthermore, the signal receiving circuit and the signal sending circuit can realize high-speed wireless information transmission from the secondary side to the primary side of the system without adding any other wireless information transmission equipment.

[0015] Furthermore, the low-pass filter in the signal receiving circuit includes: a resistor R6, a resistor R7, a capacitor C1, a capacitor C2, and a second operational amplifier AD8065; the low-pass filter can filter low-frequency signals; the two ends of the resistor R6 are respectively connected to the input end of the low-pass filter and the resistor R7, the two ends of the resistor R7 are respectively connected to the resistor R6 and the positive input end of the second operational amplifier AD8065, the two ends of the capacitor C1 are respectively connected to the positive input end of the second operational amplifier AD8065 and the ground, one end of the capacitor C2 is connected to the resistor R6 and the resistor R7, and the other end is connected to the output end of the second operational amplifier AD8065; the output end of the second operational amplifier AD8065 is connected to the output end of the low-pass filter; it is used to determine the capacitance and resistance values ​​in the circuit according to the frequency of the transmitted information for filtering;

[0016] Further, the high-pass filter in the signal receiving circuit includes: a resistor R8, a resistor R9, a capacitor C3, a capacitor C4, and a third operational amplifier AD8065; the high-pass filter can filter high-frequency signals; the two ends of the capacitor C3 are respectively connected to the input end of the high-pass filter and the capacitor C4, the two ends of the capacitor C4 are respectively connected to the capacitor C3 and the positive input end of the third operational amplifier AD8065, one end of the resistor R8 is connected to the capacitor C3 and the capacitor C4, and the other end is connected to the output end of the third operational amplifier AD8065, the two ends of the resistor R9 are respectively connected to the positive input end of the third operational amplifier AD8065 and the ground; the output end of the third operational amplifier AD8065 is connected to the output end of the high-pass filter; it is used to determine the capacitance and resistance values ​​in the circuit according to the frequency of the transmitted information for filtering;

[0017] Furthermore, the advanced phase shift module in the signal sending circuit is used to compensate for the delay in the signal processing process to achieve synchronization; the two ends of the resistor R10 are respectively connected to the input end of the advanced phase shift module and the reverse input end of the fourth operational amplifier AD8065, the two ends of the resistor R11 are respectively connected to the positive input end of the fourth operational amplifier AD8065 and the ground, the two ends of the resistor R12 are respectively connected to the reverse input end of the fourth operational amplifier AD8065 and the output end of the fourth operational amplifier AD8065, and the two ends of the capacitor C5 are respectively connected to the positive input end and of the fourth operational amplifier AD8065; the output end of the fourth operational amplifier AD8065 is connected to the output end of the advanced phase shift module;

[0018] The forward zero-crossing detection module is used to detect the signal zero-crossing point to achieve the purpose of synchronous rectification; and a hysteresis comparison circuit is used to eliminate jitter; the two ends of the resistor R13 are respectively connected to the input end of the forward zero-crossing detection module and the positive input end of the first comparator TLV3502, the two ends of the resistor R14 are respectively connected to the reverse input end of the first comparator TLV3502 and the ground, and the two ends of the resistor R15 are respectively connected to the positive input end of the first comparator TLV3502 and the output end of the first comparator TLV3502; the output end of the first comparator TLV3502 is connected to the output end of the forward zero-crossing detection module;

[0019] The forward integration module is used to produce a sawtooth wave; the two ends of the resistor R16 are respectively connected to the -5V voltage regulator and the reverse input end of the fifth operational amplifier AD8066, the two ends of the capacitor C6 are respectively connected to the reverse input end of the fifth operational amplifier AD8066 and the output end of the fifth operational amplifier AD8066, the drain of the seventh MOSFET switch tube is connected to the reverse input end of the fifth operational amplifier AD8066, the source of the seventh MOSFET switch tube is connected to the output end of the fifth operational amplifier AD8066, and the gate of the seventh MOSFET switch tube is connected to the input end of the forward integration module; the forward input end of the fifth operational amplifier AD8066 is connected to the ground, and the output end of the fifth operational amplifier AD8066 is connected to the output end of the forward integration module;

[0020] The forward waveform correction circuit is used to correct the amplitude of the sawtooth waveform; the two ends of the resistor R17 are respectively connected to the input end of the forward waveform correction circuit and the positive input end of the sixth operational amplifier AD8066, the two ends of the resistor R18 are respectively connected to the positive input end of the sixth operational amplifier AD8066 and the output end of the sixth operational amplifier AD8066, the reverse input end of the sixth operational amplifier AD8066 is connected to the ground; the output end of the sixth operational amplifier AD8066 is connected to the output end of the forward waveform correction circuit;

[0021] The forward control signal generating module is used to generate a gate signal for controlling the on and off of the fifth switch tube; a hysteresis comparison circuit is used to eliminate jitter; the two ends of the resistor R19 are respectively connected to the input end of the forward control signal generating module and the positive input end of the second comparator TLV3502, the two ends of the resistor R20 are respectively connected to the reverse input end of the second comparator TLV3502 and the ground, and the two ends of the resistor R21 are respectively connected to the positive input end of the second comparator TLV3502 and the output end of the second comparator TLV3502; the output end of the second comparator TLV3502 is connected to the output end of the forward control signal generating module;

[0022] The reverse zero-crossing detection module is used to detect the zero-crossing point of the signal to achieve the purpose of synchronous rectification; a hysteresis comparison circuit is used to eliminate jitter; the two ends of the resistor R22 are respectively connected to the input end of the reverse zero-crossing detection module and the reverse input end of the third comparator TLV3502, the two ends of the resistor R23 are respectively connected to the positive input end of the third comparator TLV3502 and the ground, and the two ends of the resistor R24 ​​are respectively connected to the reverse input end of the third comparator TLV3502 and the output end of the first comparator TLV3502; the output end of the third comparator TLV3502 is connected to the output end of the reverse zero-crossing detection module;

[0023] The reverse integration module is used to produce a sawtooth wave; the two ends of the resistor R25 are respectively connected to the -5V voltage regulator and the reverse input end of the seventh operational amplifier AD8066, the two ends of the capacitor C7 are respectively connected to the reverse input end of the seventh operational amplifier AD8066 and the output end of the seventh operational amplifier AD8066, the drain of the eighth MOSFET switch tube is connected to the reverse input end of the seventh operational amplifier AD8066, the source of the eighth MOSFET switch tube is connected to the output end of the seventh operational amplifier AD8066, and the gate of the eighth MOSFET switch tube is connected to the input end of the reverse integration module; the positive input end of the seventh operational amplifier AD8066 is connected to the ground, and the output end of the seventh operational amplifier AD8066 is connected to the output end of the reverse integration module;

[0024] The reverse waveform correction module is used to correct the amplitude of the sawtooth waveform; the two ends of the resistor R26 are respectively connected to the input end of the reverse waveform correction module and the positive input end of the eighth operational amplifier AD8066, the two ends of the resistor R27 are respectively connected to the positive input end of the eighth operational amplifier AD8066 and the output end of the eighth operational amplifier AD8066, the reverse input end of the eighth operational amplifier AD8066 is connected to the ground; the output end of the eighth operational amplifier AD8066 is connected to the output end of the reverse waveform correction module;

[0025] The reverse control signal generating module is used to generate a gate signal for controlling the on and off of the sixth switch tube; a hysteresis comparison circuit is used to eliminate jitter; the two ends of the resistor R28 are respectively connected to the input end of the reverse control signal generating module and the positive input end of the fourth comparator TLV3502, the two ends of the resistor R29 are respectively connected to the reverse input end of the fourth comparator TLV3502 and the ground, the two ends of the resistor 30 are respectively connected to the positive input end of the fourth comparator TLV3502 and the output end of the fourth comparator TLV3502; the output end of the fourth comparator TLV3502 is connected to the output end of the reverse control signal generating module.

[0026] Furthermore, the signal sending circuit processes the signal output by the current transformer and outputs a signal to control the opening and closing of the fifth switch tube S5 and the sixth switch tube S6 in the semi-bridgeless active rectifier circuit, which can not only realize synchronous rectification on the secondary side, but also send information to the primary side by controlling the microcontroller MCU in the signal sending circuit; the secondary side is one side of the semi-bridgeless active rectifier circuit, that is, the power receiving end of the wireless transmission system, and has no physical connection with the primary side; the current transformer includes an iron core, a main winding and a secondary winding, the main winding and the secondary winding are wound on the iron core, when the measured current passes through the main winding of the transformer, a secondary current proportional to the main current will be induced in the secondary winding, and by detecting the secondary current, the current in the main circuit can be indirectly measured; wherein the two ends of the main winding are connected to the secondary semi-bridgeless active rectifier circuit, and the secondary winding is connected to the input end of the signal sending circuit.

[0027] A second aspect of the present invention is a method for transmitting wireless power information simultaneously, the method comprising the following steps:

[0028] (a) The DC regulated power supply transmits power wirelessly to the load through a full-bridge inverter circuit, a semi-bridgeless active rectifier circuit and a magnetic coupling resonant network, and a wireless power transmission system is built;

[0029] (b) a current transformer collects a current signal of the semi-bridgeless active rectifier circuit, and implements synchronous rectification of the MOSFET switch tube in the semi-bridgeless active rectifier circuit through the signal sending circuit, so as to improve the efficiency of the wireless power transmission system;

[0030] (c) The microcontroller MCU in the signal sending circuit modulates the signal in the signal sending circuit, controls the duty cycle of the output PWM signal, changes the conduction duty cycle of the two MOSFET switch tubes in the semi-bridgeless active rectifier circuit within the operating frequency cycle, and the information is sent on the secondary side;

[0031] (d) The signal receiving circuit is connected to the full-bridge inverter circuit, and receives the information transmitted from the secondary side to the primary side by detecting the current in the full-bridge inverter circuit, thereby realizing synchronous transmission of power information.

[0032] According to the specific embodiments provided by the present invention, the present invention discloses the following technical effects:

[0033] The present invention discloses a set of wireless power information simultaneous transmission devices and methods suitable for charging occasions of low-power electrical equipment. Under the working frequency of 1 MHz, active rectification hardware circuits, signal transmission and signal reception hardware circuits are designed to realize 1 kHz frequency communication from the secondary side to the primary side.

[0034] The DC regulated power supply wirelessly transmits electric energy to the load through the full-bridge inverter circuit, the magnetic coupling resonant network, and the semi-bridgeless active rectifier circuit, thereby building a wireless power transmission system.

[0035] Furthermore, the current transformer collects the current signal of the semi-bridgeless active rectifier circuit, and implements synchronous rectification of the MOSFET switch tube in the semi-bridgeless active rectifier circuit through the signal sending circuit, thereby improving the efficiency of the wireless power transmission system.

[0036] Furthermore, the operating frequency of the wireless power transmission system is 1 MHz.

[0037] Furthermore, the microcontroller MCU in the signal sending circuit modulates the signal in the signal sending circuit, controls the duty cycle of the output PWM signal, changes the conduction duty cycle of the two MOSFET switching tubes in the semi-bridgeless active rectifier circuit within the operating frequency cycle, and the information is sent on the secondary side.

[0038] Furthermore, the signal receiving circuit is connected to the full-bridge inverter circuit, and receives information transmitted from the secondary side to the primary side by detecting the current in the full-bridge inverter circuit, thereby achieving synchronous transmission of power information.

[0039] Furthermore, the frequency of the signal transmitted from the secondary side to the primary side is 1 kHz.

[0040] The beneficial effects of the present invention are as follows: the present invention uses a phase-shifted semi-bridgeless active rectifier circuit (S-BAR) on the secondary side of a traditional wireless power transmission system, and realizes high-frequency wireless power information simultaneous transmission through hardware circuit design. Based on the present invention, electric energy can be transmitted from the primary side to the secondary side without contact, and information can be transmitted from the secondary side to the primary side at the same time. The present invention no longer relies on physical wires, reduces metal resource consumption and safety hazards, and is more convenient and flexible; compared with traditional wireless power transmission devices, the present invention can realize the simultaneous transmission of power and information, saving the cost of additional information transmission devices. BRIEF DESCRIPTION OF THE DRAWINGS

[0041] In order to more clearly illustrate the technical solution of the present invention, the following is a brief introduction to the drawings required for use in the description of the embodiments. Obviously, the drawings described below are only some embodiments of the present invention. For ordinary technicians in this field, other drawings can be obtained based on these drawings without paying creative work.

[0042] Figure 1 This is a system block diagram of a wireless power information simultaneous transmission device proposed by the present invention;

[0043] Figure 2The switch state conversion analysis and current path of a secondary side of a wireless power information simultaneous transmission device proposed by the present invention, wherein (a) shows the working mode of the secondary side from t0 to t1, (b) shows the working mode of the secondary side from t1 to t2, (c) shows the working mode of the secondary side from t2 to t3, and (d) shows the working mode of the secondary side from t3 to t4;

[0044] Figure 3 The input voltage v of the secondary side semi-bridgeless active rectifier circuit in a typical embodiment of the wireless power information simultaneous transmission device proposed by the present invention is S Waveform diagram of

[0045] Figure 4 A simplified schematic diagram (a) and a mutual inductance circuit model schematic diagram (b) of a wireless power transmission system with a series-series compensation structure in a typical embodiment of a wireless power information simultaneous transmission device proposed by the present invention;

[0046] Figure 5 A specific implementation circuit of a signal receiving circuit in a typical embodiment of a wireless power information simultaneous transmission device proposed by the present invention;

[0047] Figure 6 A specific implementation device of a current transformer in a typical embodiment of a wireless power information simultaneous transmission device proposed by the present invention;

[0048] Figure 7 A specific implementation circuit of a signal sending circuit in a typical embodiment of a wireless power information simultaneous transmission device proposed by the present invention;

[0049] Figure 8 A schematic diagram of the waveforms of the primary side signal, the secondary side current signal and the current transformer output signal in a wireless power transmission system in a typical embodiment of a wireless power information simultaneous transmission device proposed by the present invention;

[0050] Fig. 9 A waveform diagram of a signal transmission circuit in a typical embodiment of a wireless power information simultaneous transmission device proposed by the present invention;

[0051] Reference numerals: DC regulated power supply-1; full-bridge inverter circuit-2; semi-bridgeless active rectifier circuit-3; magnetic coupling resonant network-4; load R L -5; signal receiving circuit-6; current transformer-7; signal sending circuit-8. DETAILED DESCRIPTION

[0052] In order to make the structure and advantages of the present invention more clear, the structure of the present invention will be further described below in conjunction with the accompanying drawings:

[0053] like Figure 1As shown, the present invention provides a wireless power information transmission device, including a DC regulated power supply 1, a full-bridge inverter circuit 2, a semi-bridgeless active rectifier circuit 3, a magnetic coupling resonant network 4, and a load R L 5, signal receiving circuit 6, current transformer 7 and signal sending circuit 8; the DC regulated power supply 1 passes through the full-bridge inverter circuit 2 and the magnetic coupling resonant network 4 in sequence; the semi-bridgeless active rectifier circuit 3 and the load R L 5; the signal receiving circuit 6 is connected to the full-bridge inverter circuit 2; the current transformer 7 is respectively connected to the semi-bridgeless active rectifier circuit 3 and the signal sending circuit 8; the signal sending circuit 8 is respectively connected to the current transformer 7 and the second end of the fifth switch tube S5 and the second end of the sixth switch tube S6 in the semi-bridgeless active rectifier circuit 3;

[0054] The semi-bridgeless active rectifier circuit 3 includes: a first diode D1, a second diode D2, a fifth switch tube S5, a sixth switch tube S6 and a fourth capacitor C L The cathode of the first diode D1 is connected to the cathode of the second diode D2 and the fourth capacitor C L One end and load R L 5, the anode of the first diode D1 is connected to the first end of the fifth switch tube S5, and the third end of the fifth switch tube S5 is connected to the third end of the sixth switch tube S6 and the fourth capacitor C L The other end and the load R L 5, the anode of the second diode D2 is connected to the first end of the sixth switch tube S6, and the anode of the first diode D1, the first end of the fifth switch tube S5, the anode D2 of the second diode and the first end of the sixth switch tube S6 are respectively connected to the magnetic coupling resonant network 4;

[0055] The signal receiving circuit 6 comprises: a sampling resistor R, a differential circuit module, a low-pass filter and a high-pass filter, wherein the sampling resistor R is connected in series with a DC regulated power supply and a full-bridge inverter circuit on the primary side, and the primary side is one side of the full-bridge inverter circuit, i.e., the power transmitting end of the wireless transmission system; the two ends of the sampling resistor R are respectively connected to the positive and negative inputs of the differential circuit module, and the receiving signal is output through the low-pass filter and the high-pass filter;

[0056] The signal sending circuit 8 includes: a microcontroller MCU, an advanced phase shift module, a forward zero-crossing detection module, a forward integration module, a forward waveform correction module, a forward control signal generation module, a reverse zero-crossing detection module, a reverse integration module, a reverse waveform correction module, a reverse control signal generation module, a drive circuit module-1, a drive circuit module-2, a drive circuit module-3 and a drive circuit module-4;

[0057] The side of the full-bridge inverter circuit 2 is called the primary side, and the side of the semi-bridgeless active rectifier circuit 3 is called the secondary side. The primary side and the secondary side have no physical connection, and are the power transmitting end (primary side) and the receiving end (secondary side) of the wireless transmission system; specifically: in the wireless power transmission system, the primary side and the secondary side refer to the two main electromagnetic coupling parts in the system. The primary side (Primary Side) is the transmitting part of the energy transmission, usually connected to the power supply, responsible for generating the electromagnetic field. The secondary side (Secondary Side) is the receiving part, which receives the electromagnetic energy from the primary side and converts it into electrical energy or other forms of energy. The two interact through electromagnetic induction to achieve contactless energy transmission.

[0058] The working mode of the semi-bridgeless active rectifier circuit 3 is as follows: Figure 2 As shown: Mode 1 [t0-t1]: During this time interval, the switches S5 and S6 are turned off, and the current flows in the forward direction, flowing through the diode D1 and the body diode of the switch S6. The current path is as follows: Figure 2 As shown in (a), in this mode, energy is transferred to the load; Mode 2 [t1-t2]: In this interval, switch tube S6 is turned on, and the current path is determined by the current direction. The current flows in the negative direction and flows through the body diodes of switch tubes S5 and S6. The current path is as follows Figure 2 (b) shows that in this mode, energy cannot be transferred to the load; Mode 3 [t2-t3]: During this time interval, switches S5 and S6 are turned off, and the current flows in the negative direction, which will flow through diode D2 and the body diode of switch S5. The current path is as follows: Figure 2 (c) shows that in this mode, energy is transferred to the load; Mode 4 [t3-t4]: In this interval, switch S5 is turned on. The current path is determined by the current direction. If the current flows in the negative direction, it will flow through the body diodes of switch S5 and switch S6. The current path is as follows: Figure 2 As shown in (d), in this mode, energy cannot be transferred to the load;

[0059] The input signal waveform of the semi-bridgeless active rectifier circuit 3 is as follows: Figure 3 As shown, in each cycle, the energy is transferred to the load (mode 1 and mode 3) with a duty cycle of D, and the energy cannot be transferred to the load (mode 2 and mode 4) with a duty cycle of (1-D). In this mode, the secondary side conversion relationship is similar to that of the traditional Buck converter. After Fourier transform, v s Fundamental amplitude V s1 The values ​​are: Where V o is the effective value of the voltage across the load. By calculating the power conservation principle, the equivalent resistance R can be obtained. e for: Where Vs is the effective value of the secondary voltage, I s is the effective value of the secondary current, R L is the actual resistance of the load;

[0060] For the convenience of calculation, the wireless power transmission system with series-series compensation structure is simplified. Assumptions: When the resonant circuit has a high quality factor, the square wave output by the full-bridge inverter circuit does not consider its higher harmonic components, and only retains the sine fundamental component. Therefore, it is equivalent to a DC voltage source with a frequency equal to the switching frequency and an amplitude equal to the input voltage. For the secondary rectifier circuit, assuming that the output filter capacitor is large enough and the output voltage is constant, the load resistance and the uncontrolled rectifier circuit are approximately equivalent to the resistance R e , which satisfies the actual load relationship;

[0061] The simplified schematic diagram is as follows Figure 4 (a) shows the schematic diagram of the mutual inductance circuit model. Figure 4 (b)

[0062] Matching capacitor C in series-series compensation wireless power transmission system p and C s Satisfies the following relationship:

[0063] Where f is the switching signal frequency, L p is the inductance of the primary coupling coil, L s is the inductance of the secondary coupling coil;

[0064] In the above model, the following equation can be obtained according to the KVL law:

[0065] where ω o represents the resonant angular frequency, M represents the mutual inductance of the magnetic coupling coil, V p Represents the output voltage vector of the primary full-bridge inverter circuit, I p The output current vector of the primary full-bridge inverter circuit, R p Indicates the parasitic resistance of the primary resonant network, I s Represents the output current vector of the secondary full-bridge inverter circuit, R s Indicates the parasitic resistance of the secondary resonant network;

[0066] With capacitor C p and C s Substituting the satisfied relationship back into the above formula, we can derive: V p =jω o MI s +I p R p, jω o MI p =-I s (R e +R s );

[0067] The secondary current can be obtained by solving the above equation: for:

[0068] The primary current can be deduced from the above formula: for:

[0069] From this, we can know the current I p And the equivalent resistance R e The arithmetic relationship between e The relationship between the energy transferred to the load in each cycle (mode 1 and mode 3) and the duty cycle D is Therefore, we can monitor the primary current data to obtain the change of the secondary duty cycle D;

[0070] Therefore, it is only necessary to control the duty cycle D on the secondary side and detect the current I on the primary side. p By simply changing the size of , the information can be transmitted from the secondary side to the primary side, completing the simultaneous transmission of power information.

[0071] Figure 5 A signal receiving solution provided by an embodiment of the present invention is a signal receiving circuit 6, comprising: a differential circuit (a), a low-pass filter (b) and a high-pass filter (c), wherein:

[0072] In one embodiment of the present invention, Figure 5 As shown, the differential circuit (a) includes: resistors R1, R2, R3, R4, R5, and a first operational amplifier AD8065. The differential circuit (a) can be used as a differential input for signals, and can also amplify and reduce signals. The two ends of the resistor R1 are respectively connected to the positive and negative input terminals v of the differential circuit (a). in + and v in - connected, the two ends of the resistor R2 are respectively connected to the positive input terminal v of the differential circuit (a) in + is connected to the positive input terminal of the first operational amplifier AD8065, and the two ends of the resistor R3 are respectively connected to the negative input terminal v of the differential circuit (a) in - and the inverting input terminal of the first operational amplifier AD8065, and the two ends of the resistor R3 are respectively connected to the negative input terminal v of the differential circuit (a) in- is connected to the inverting input terminal of the first operational amplifier AD8065, the two ends of the resistor R4 are respectively connected to the inverting input terminal of the first operational amplifier AD8065 and the ground, the two ends of the resistor R5 are respectively connected to the positive input terminal of the first operational amplifier AD8065 and the output terminal of the first operational amplifier AD8065. The output terminal of the first operational amplifier AD8065 is connected to the output terminal of the differential circuit (a).

[0073] In one embodiment of the present invention, Figure 5 As shown, the low-pass filter (b) includes: a resistor R6, a resistor R7, a capacitor C1, a capacitor C2, and a second operational amplifier AD8065. The low-pass filter (b) can filter low-frequency signals. The two ends of the resistor R6 are respectively connected to the input end of the low-pass filter (b) and the resistor R7, the two ends of the resistor R7 are respectively connected to the resistor R6 and the positive input end of the second operational amplifier AD8065, the two ends of the capacitor C1 are respectively connected to the positive input end of the second operational amplifier AD8065 and the ground, one end of the capacitor C2 is connected to the resistor R6 and the resistor R7, and the other end is connected to the output end of the second operational amplifier AD8065. The output end of the second operational amplifier AD8065 is connected to the output end of the low-pass filter (b). The capacitor and resistor values ​​in the circuit are determined according to the frequency of the transmitted information to achieve the filtering purpose.

[0074] In one embodiment of the present invention, Figure 5 As shown, the high-pass filter (c) includes: a resistor R8, a resistor R9, a capacitor C3, a capacitor C4, and a third operational amplifier AD8065. The high-pass filter (c) can filter high-frequency signals. The two ends of the capacitor C3 are respectively connected to the input end of the high-pass filter (c) and the capacitor C4, the two ends of the capacitor C4 are respectively connected to the capacitor C3 and the positive input end of the third operational amplifier AD8065, one end of the resistor R8 is connected to the capacitor C3 and the capacitor C4, and the other end is connected to the output end of the third operational amplifier AD8065, and the two ends of the resistor R9 are respectively connected to the positive input end of the third operational amplifier AD8065 and the ground. The output end of the third operational amplifier AD8065 is connected to the output end of the high-pass filter (c). The capacitor and resistor values ​​in the circuit are determined according to the frequency of the transmitted information to achieve the filtering purpose.

[0075] Figure 6A transformer as a current transformer 7 provided in an embodiment of the present invention comprises: an iron core, a main winding and a secondary winding. The main winding and the secondary winding are wound on the iron core. When the current to be measured passes through the main winding of the transformer, it will induce a secondary current proportional to the main current in the secondary winding. By detecting the secondary current, the current in the main circuit can be indirectly measured. The two ends of the main winding are connected to the secondary semi-bridgeless active rectifier circuit 3, and the secondary winding is connected to the input end of the signal sending circuit.

[0076] Figure 7 A signal transmission scheme provided by an embodiment of the present invention is used as a signal receiving circuit (8), comprising: an advanced phase shift module (d), a forward zero-crossing detection module (e), a forward integration module (f), a forward waveform correction circuit (g), a forward control signal generation module (h), a reverse zero-crossing detection module (i), a reverse integration module (j), a reverse waveform correction module (k), a reverse control signal generation module (l), a drive circuit module-1, a drive circuit module-2 (m), a drive circuit module-3, a drive circuit module-4 (n), and a microcontroller MCU (o), wherein:

[0077] In one embodiment of the present invention, Figure 7 As shown, the advanced phase shift module (d) includes: a resistor R10, a resistor R11, a resistor R12, a capacitor C5, and a fourth operational amplifier AD8065. The advanced phase shift module (d) is used to compensate for the delay in the signal processing process to achieve the purpose of accurate synchronization. The two ends of the resistor R10 are respectively connected to the input end of the advanced phase shift module (d) and the reverse input end of the fourth operational amplifier AD8065, the two ends of the resistor R11 are respectively connected to the positive input end and ground of the fourth operational amplifier AD8065, the two ends of the resistor R12 are respectively connected to the reverse input end of the fourth operational amplifier AD8065 and the output end of the fourth operational amplifier AD8065, and the two ends of the capacitor C5 are respectively connected to the positive input end and of the fourth operational amplifier AD8065. The output end of the fourth operational amplifier AD8065 is connected to the output end of the advanced phase shift module (d).

[0078] Furthermore, R 10 =R 12 , according to the virtual short and virtual break theorem, the relationship between the input signal x and the output signal y is:

[0079]

[0080] Where ω represents the signal frequency angular rate;

[0081] Further, the output y can be simplified to the input x as follows:

[0082] Furthermore, it can be seen that the gain A of the circuit module is fixed to 1:

[0083] Furthermore, the circuit leads the phase shift angle With the circuit frequency ω, capacitor C5 and resistor R 11 The relationship is as follows:

[0084]

[0085] Further simplification can be obtained: Used to determine the capacitance C5 and the resistance R 11 value to achieve accurate angle of leading phase shift compensation.

[0086] In one embodiment of the present invention, Figure 7 As shown, the forward zero-crossing detection module (e) includes: a resistor R13, a resistor R14, a resistor R15, and a first comparator TLV3502. The forward zero-crossing detection module (e) is used to detect the zero-crossing point of the signal to achieve the purpose of synchronous rectification; a hysteresis comparison circuit is used to achieve the purpose of eliminating jitter. The two ends of the resistor R13 are respectively connected to the input end of the forward zero-crossing detection module (e) and the positive input end of the first comparator TLV3502, the two ends of the resistor R14 are respectively connected to the reverse input end of the first comparator TLV3502 and the ground, and the two ends of the resistor R15 are respectively connected to the positive input end of the first comparator TLV3502 and the output end of the first comparator TLV3502. The output end of the first comparator TLV3502 is connected to the output end of the forward zero-crossing detection module (e).

[0087] In one embodiment of the present invention, Figure 7 As shown, the forward integration module (f) includes: a resistor R16, a capacitor C6, a seventh MOSFET switch tube, and a fifth operational amplifier AD8066. The forward integration module (f) is used to produce a sawtooth wave. The two ends of the resistor R16 are respectively connected to the -5V voltage regulator and the reverse input end of the fifth operational amplifier AD8066, the two ends of the capacitor C6 are respectively connected to the reverse input end of the fifth operational amplifier AD8066 and the output end of the fifth operational amplifier AD8066, the drain of the seventh MOSFET switch tube is connected to the reverse input end of the fifth operational amplifier AD8066, the source of the seventh MOSFET switch tube is connected to the output end of the fifth operational amplifier AD8066, and the gate of the seventh MOSFET switch tube is connected to the input end of the forward integration module (f). The forward input end of the fifth operational amplifier AD8066 is connected to the ground, and the output end of the fifth operational amplifier AD8066 is connected to the output end of the forward integration module (f).

[0088] In one embodiment of the present invention, Figure 7 As shown, the forward waveform correction circuit (g) includes: a resistor R17, a resistor R18, and a sixth operational amplifier AD8066. The forward waveform correction circuit (g) is used to correct the amplitude of the sawtooth waveform. The two ends of the resistor R17 are respectively connected to the input end of the forward waveform correction circuit (g) and the positive input end of the sixth operational amplifier AD8066, the two ends of the resistor R18 are respectively connected to the positive input end of the sixth operational amplifier AD8066 and the output end of the sixth operational amplifier AD8066, and the reverse input end of the sixth operational amplifier AD8066 is connected to the ground. The output end of the sixth operational amplifier AD8066 is connected to the output end of the forward waveform correction circuit (g).

[0089] In one embodiment of the present invention, Figure 7 As shown, the forward control signal generating module (h) includes: a resistor R19, a resistor R20, a resistor R21, and a second comparator TLV3502. The forward control signal generating module (h) is used to generate a gate signal for controlling the opening and closing of the fifth switch tube; a hysteresis comparison circuit is used to eliminate jitter. The two ends of the resistor R19 are respectively connected to the input end of the forward control signal generating module (h) and the positive input end of the second comparator TLV3502, the two ends of the resistor R20 are respectively connected to the reverse input end of the second comparator TLV3502 and the ground, and the two ends of the resistor R21 are respectively connected to the positive input end of the second comparator TLV3502 and the output end of the second comparator TLV3502. The output end of the second comparator TLV3502 is connected to the output end of the forward control signal generating module (h).

[0090] In one embodiment of the present invention, Figure 7 As shown, the reverse zero-crossing detection module (i) includes: a resistor R22, a resistor R23, a resistor R24, and a third comparator TLV3502. The reverse zero-crossing detection module (i) is used to detect the zero-crossing point of the signal to achieve the purpose of synchronous rectification; a hysteresis comparison circuit is used to achieve the purpose of eliminating jitter. The two ends of the resistor R22 are respectively connected to the input end of the reverse zero-crossing detection module (i) and the reverse input end of the third comparator TLV3502, the two ends of the resistor R23 are respectively connected to the positive input end and ground of the third comparator TLV3502, and the two ends of the resistor R24 ​​are respectively connected to the reverse input end of the third comparator TLV3502 and the output end of the first comparator TLV3502. The output end of the third comparator TLV3502 is connected to the output end of the reverse zero-crossing detection module (i).

[0091] In one embodiment of the present invention, Figure 7As shown, the reverse integration module (j) includes: a resistor R25, a capacitor C7, an eighth MOSFET switch tube, and a seventh operational amplifier AD8066. The reverse integration module (j) is used to produce a sawtooth wave. The two ends of the resistor R25 are respectively connected to the -5V voltage regulator and the reverse input end of the seventh operational amplifier AD8066, the two ends of the capacitor C7 are respectively connected to the reverse input end of the seventh operational amplifier AD8066 and the output end of the seventh operational amplifier AD8066, the drain of the eighth MOSFET switch tube is connected to the reverse input end of the seventh operational amplifier AD8066, the source of the eighth MOSFET switch tube is connected to the output end of the seventh operational amplifier AD8066, and the gate of the eighth MOSFET switch tube is connected to the input end of the reverse integration module (j). The positive input end of the seventh operational amplifier AD8066 is connected to the ground, and the output end of the seventh operational amplifier AD8066 is connected to the output end of the reverse integration module (j).

[0092] In one embodiment of the present invention, Figure 7 As shown, the reverse waveform correction module (k) includes: a resistor R26, a resistor R27, and an eighth operational amplifier AD8066. The reverse waveform correction module (k) is used to correct the amplitude of the sawtooth waveform. The two ends of the resistor R26 are respectively connected to the input end of the reverse waveform correction module (k) and the positive input end of the eighth operational amplifier AD8066, the two ends of the resistor R27 are respectively connected to the positive input end of the eighth operational amplifier AD8066 and the output end of the eighth operational amplifier AD8066, and the reverse input end of the eighth operational amplifier AD8066 is connected to the ground. The output end of the eighth operational amplifier AD8066 is connected to the output end of the reverse waveform correction module (k).

[0093] In one embodiment of the present invention, Figure 7 As shown, the reverse control signal generating module reverse control signal generating module 1 includes: resistor R28, resistor R29, resistor R30, and fourth comparator TLV3502. The reverse control signal generating module reverse control signal generating module 1 is used to generate a gate signal for controlling the opening and closing of the sixth switch tube; a hysteresis comparison circuit is used to eliminate jitter. The two ends of the resistor R28 are respectively connected to the input end of the reverse control signal generating module reverse control signal generating module 1 and the positive input end of the fourth comparator TLV3502, the two ends of the resistor R29 are respectively connected to the reverse input end of the fourth comparator TLV3502 and the ground, and the two ends of the resistor 30 are respectively connected to the positive input end of the fourth comparator TLV3502 and the output end of the fourth comparator TLV3502. The output end of the fourth comparator TLV3502 is connected to the output end of the reverse control signal generating module reverse control signal generating module 1.

[0094] In one embodiment of the present invention, Figure 7 As shown, the driving circuit module 1 (m) and the driving circuit module 2 (m) include: a first driving chip UCC27524. The driving circuit module 1 (m) and the driving circuit module 2 (m) are used to provide sufficient current to charge and discharge the gate charge of the MOSFET, ensuring that the MOSFET can switch quickly and reduce power loss when turned on. The VDD pin of the first driver chip UCC27524 is connected to a 5V voltage regulator, the GND pin of the first driver chip UCC27524 is connected to the ground, the ENA pin of the first driver chip UCC27524 is connected to a 5V voltage regulator, the INA pin of the first driver chip UCC27524 is connected to the output end of the forward zero-crossing detection module (e), the OUTA pin of the first driver chip UCC27524 is connected to the input end of the forward integration module (f), the ENB pin of the first driver chip UCC27524 is connected to a 5V voltage regulator, the INB pin of the first driver chip UCC27524 is connected to the output end of the reverse zero-crossing detection module (i), and the OUTB pin of the first driver chip UCC27524 is connected to the reverse integration module (j). The output end of the fourth comparator TLV3502 is connected to the output end of the reverse control signal generation module 1 of the reverse control signal generation module.

[0095] In one embodiment of the present invention, Figure 7As shown, the driving circuit module 3 (n) and the driving circuit module 4 (n) include: a second driving chip UCC27524. The driving circuit module 3 (n) and the driving circuit module 4 (n) are used to provide sufficient current to charge and discharge the gate charge of the MOSFET, ensuring that the MOSFET can switch quickly and reduce power loss when turned on. The VDD pin of the second driver chip UCC27524 is connected to a 5V voltage regulator, the GND pin of the second driver chip UCC27524 is connected to ground, the ENA pin of the second driver chip UCC27524 is connected to a 5V voltage regulator, the INA pin of the second driver chip UCC27524 is connected to the output end of the forward control signal generating module (h), the OUTA pin of the second driver chip UCC27524 is connected to the gate of the fifth switch tube in the semi-bridgeless active rectifier circuit 3, the ENB pin of the second driver chip UCC27524 is connected to a 5V voltage regulator, the INB pin of the second driver chip UCC27524 is connected to the output end of the reverse control signal generating module (l) of the reverse control signal generating module, and the OUTB pin of the second driver chip UCC27524 is connected to the gate of the sixth switch tube in the semi-bridgeless active rectifier circuit (3). The output end of the fourth comparator TLV3502 is connected to the output end of the reverse control signal generating module (1).

[0096] In one embodiment of the present invention, Figure 7 As shown, the microcontroller MCU (o) includes: a main control chip STM32G431C8T6, whose output end is connected to a forward control signal generating module (h) and a reverse control signal generating module (l).

[0097] Figure 8 FIG. 1 is a schematic diagram of waveforms of primary side signals, secondary side current signals and current transformer output signals in a wireless power transmission system in a typical embodiment of a wireless power information simultaneous transmission device proposed by the present invention, u gS1 、u gS2 、u gS3 、u gS4 It is the gate control signal of the four switches on the primary side, converting DC into square wave v p The driving signal of the switch tube adopts a square wave signal with a fixed duty cycle, and the upper and lower tubes are complementary. S is the secondary current waveform, that is, the current waveform in the main winding, v S It is the voltage waveform measured by the current transformer.

[0098] like Figure 7 , Figure 8 and 9 As shown, Fig. 9This is a waveform diagram of a signal transmission circuit in a typical embodiment of a wireless power information transmission device proposed by the present invention. The input end of the signal transmission circuit is connected to the output end of the current transformer 7. The signal v S Input the advanced phase shift module (d), output the phase shifted signal v S ′, the signal v S ' Input the positive zero-crossing detection module (e), the output signal v gate_1 , the signal v gate_1 After being driven by the driving circuit modules 1 and 2 (m), the output signal is input into the forward integration module (f), and then input into the forward waveform correction circuit (g), and the sawtooth wave signal v is output. sawtooth_1 , the signal v sawtooth_1 Input positive control signal generating module (h), the microcontroller MCU (o) output signal V REF Input the forward control signal generation module (h), the two are compared and the output PWM signal u gS5 , the PWM signal u gS5 After being driven by the driving circuit modules 3, 4 (n), the gate driving signal v is output S5 , the gate drive signal v S5 The gate of the fifth switch tube in the semi-bridgeless active rectifier circuit 3 is input; the signal v S 'Input the reverse zero-crossing detection module (i), the output signal v gate_2 , the signal v gate_2 After being driven by the driving circuit modules 1 and 2 (m), the output signal is input into the reverse integration module (j), and then input into the reverse waveform correction module (k) to output the sawtooth wave signal v sawtooth_2 , the signal v sawtooth_2 Input reverse control signal generating module reverse control signal generating module 1, the microcontroller MCU (o) output signal V REF Input reverse control signal generation module reverse control signal generation module 1, the two compare and output PWM signal u gS6 , the PWM signal u gS6 After being driven by the driving circuit modules 3, 4 (n), the gate driving signal v is output S6 , the gate drive signal v S6 Input to the gate of the sixth switch tube in the semi-bridgeless active rectifier circuit (3);

[0099] Assume that the sawtooth wave signal v sawtooth_1 and v sawtooth_2 The maximum value is V MAX , then the microcontroller MCU(o) outputs a signal V REF The relationship between the duty cycle D during which energy is transferred to the load (mode 1 and mode 3) is:

[0100]

[0101] The above specific circuit can control the microcontroller MCU (o) to output a signal V REF The size of the current is used to control the size of the primary full-bridge inverter circuit, thereby transmitting the information of the secondary side to the primary side, realizing the simultaneous transmission of high-frequency power information.

[0102] Optionally, the first switch tube, the second switch tube, the third switch tube, the fourth switch tube, the fifth switch tube, the sixth switch tube, the seventh switch tube and the eighth switch tube are all MOSFETs, the first end is a drain, the second end is a gate, and the third end is a source.

[0103] Optionally, the models of the first switch tube, the second switch tube, the third switch tube and the fourth switch tube are GS66508T; the models of the fifth switch tube, the sixth switch tube, the seventh switch tube and the eighth switch tube are IAUZ18N10S5L420ATMA1.

[0104] Optionally, the first diode and the second diode are of model STPSC406B-TR.

[0105] Optionally, the rated voltage of the DC regulated power supply 1 is 30V.

[0106] The above descriptions are merely embodiments of the present invention and are not intended to limit the present invention. Any modifications, equivalent substitutions, improvements, etc. made within the spirit and principles of the present invention should be included in the protection scope of the present invention.

Claims

1. A wireless power information simultaneous transmission device, characterized in that: The device comprises a DC voltage-stabilized power supply (1), a full-bridge inverter circuit (2), a semi-bridgeless active rectifier circuit (3), a magnetic coupling resonant network (4), a load R L (5), a signal receiving circuit (6), a current transformer (7) and a signal sending circuit (8); the DC regulated power supply (1) passes through a full-bridge inverter circuit (2), a magnetic coupling resonant network (4) in sequence; the semi-bridgeless active rectifier circuit (3) and a load R L (5); the signal receiving circuit (6) is connected to the full-bridge inverter circuit (2); the current transformer (7) is respectively connected to the semi-bridgeless active rectifier circuit (3) and the signal sending circuit (8); the signal sending circuit (8) is respectively connected to the current transformer (7) and the second end of the fifth switch tube S5 and the second end of the sixth switch tube S6 in the semi-bridgeless active rectifier circuit (3); The semi-bridgeless active rectifier circuit (3) comprises: a first diode D1, a second diode D2, a fifth switch tube S5, a sixth switch tube S6 and a fourth capacitor C L The cathode of the first diode D1 is connected to the cathode of the second diode D2 and the fourth capacitor C L One end and load R L (5), the anode of the first diode D1 is connected to the first end of the fifth switch tube S5, and the third end of the fifth switch tube S5 is connected to the third end of the sixth switch tube S6 and the fourth capacitor C L The other end and the load R L (5), the anode of the second diode D2 is connected to the first end of the sixth switch tube S6, the anode of the first diode D1, the first end of the fifth switch tube S5, the anode D2 of the second diode and the first end of the sixth switch tube S6 are respectively connected to the magnetic coupling resonant network (4); The signal receiving circuit (6) comprises: a sampling resistor R, a differential circuit module, a low-pass filter and a high-pass filter, wherein the sampling resistor R is connected in series with a DC regulated power supply and a full-bridge inverter circuit on the primary side, wherein the primary side is one side of the full-bridge inverter circuit, i.e., the power transmitting end of the wireless transmission system; the two ends of the sampling resistor R are respectively connected to the positive and negative inputs of the differential circuit module, and the receiving signal is output through the low-pass filter and the high-pass filter; The signal transmission circuit (8) comprises: a microcontroller MCU, an advanced phase shift module, a forward zero-crossing detection module, a forward integration module, a forward waveform correction module, a forward control signal generation module, a reverse zero-crossing detection module, a reverse integration module, a reverse waveform correction module, a reverse control signal generation module, a drive circuit module 1, a drive circuit module 2, a drive circuit module 3 and a drive circuit module 4; The leading phase shift module includes: resistor R10, resistor R11, resistor R12, capacitor C5 and fourth operational amplifier AD8065; the forward zero-crossing detection module includes: resistor R13, resistor R14, resistor R15 and first comparator TLV3502; the forward integration module includes: resistor R16, capacitor C6, seventh MOSFET switch tube and fifth operational amplifier AD8066; the forward waveform correction circuit includes: resistor R17, resistor R18 and sixth operational amplifier AD8066; the forward control signal generation module includes: resistor R19, resistor R20, resistor R21 and second comparator TLV3502; the reverse zero-crossing detection module includes: resistor R22, resistor R23, resistor R24 and the third comparator TLV3502; the reverse integration module includes: resistor R25, capacitor C7, the eighth MOSFET switch tube and the seventh operational amplifier AD8066; the reverse waveform correction module includes: resistor R26, resistor R27 and the eighth operational amplifier AD8066; the reverse control signal generation module includes: resistor R28, resistor R29, resistor R30 and the fourth comparator TLV3502; the drive circuit module 1 and the drive circuit module 2 are the first drive chip UCC27524, and the drive circuit module 3 and the drive circuit module 4 are the second drive chip UCC27524; the microcontroller MCU is the main control chip STM32G431C8T6.

2. A wireless power information simultaneous transmission device as claimed in claim 1, characterized in that: The rated voltage of the DC regulated power supply (1) is 30V.

3. A wireless power information simultaneous transmission device as claimed in claim 1, characterized in that: The operating frequencies of the full-bridge inverter circuit (2), the semi-bridgeless active rectification circuit (3) and the magnetic coupling resonance network (4) all need to reach above 1 MHz.

4. A wireless power information simultaneous transmission device as claimed in claim 3, characterized in that: The semi-bridgeless active rectification circuit (3) can realize high-frequency synchronous rectification at the operating frequency.

5. The wireless power information simultaneous transmission device according to claim 1, characterized in that: The signal receiving circuit (6) and the signal sending circuit (8) can realize high-speed wireless information transmission from the secondary side to the primary side of the system without adding any other wireless information transmission equipment.

6. The wireless power information simultaneous transmission device according to claim 1, characterized in that: The low-pass filter in the signal receiving circuit (6) comprises: a resistor R6, a resistor R7, a capacitor C1, a capacitor C2, and a second operational amplifier AD8065; the low-pass filter can filter low-frequency signals; the two ends of the resistor R6 are respectively connected to the input end of the low-pass filter and the resistor R7, the two ends of the resistor R7 are respectively connected to the resistor R6 and the positive input end of the second operational amplifier AD8065, the two ends of the capacitor C1 are respectively connected to the positive input end of the second operational amplifier AD8065 and the ground, one end of the capacitor C2 is connected to the resistor R6 and the resistor R7, and the other end is connected to the output end of the second operational amplifier AD8065; the output end of the second operational amplifier AD8065 is connected to the output end of the low-pass filter; and the method is used to determine the capacitance and resistance values ​​in the circuit according to the frequency of the transmitted information for filtering.

7. The wireless power information simultaneous transmission device according to claim 1, characterized in that: The high-pass filter in the signal receiving circuit (6) comprises: a resistor R8, a resistor R9, a capacitor C3, a capacitor C4, and a third operational amplifier AD8065; the high-pass filter can filter high-frequency signals; the two ends of the capacitor C3 are respectively connected to the input end of the high-pass filter and the capacitor C4, the two ends of the capacitor C4 are respectively connected to the capacitor C3 and the positive input end of the third operational amplifier AD8065, one end of the resistor R8 is connected to the capacitor C3 and the capacitor C4, and the other end is connected to the output end of the third operational amplifier AD8065, the two ends of the resistor R9 are respectively connected to the positive input end of the third operational amplifier AD8065 and the ground; the output end of the third operational amplifier AD8065 is connected to the output end of the high-pass filter; and the method for filtering is used to determine the capacitance and resistance values ​​in the circuit according to the frequency of the transmitted information.

8. The wireless power information simultaneous transmission device according to claim 1, characterized in that: The advanced phase shift module in the signal transmission circuit (8) is used to compensate for the delay in the signal processing process, so as to achieve synchronization; the two ends of the resistor R10 are respectively connected to the input end of the advanced phase shift module and the reverse input end of the fourth operational amplifier AD8065, the two ends of the resistor R11 are respectively connected to the positive input end of the fourth operational amplifier AD8065 and the ground, the two ends of the resistor R12 are respectively connected to the reverse input end of the fourth operational amplifier AD8065 and the output end of the fourth operational amplifier AD8065, the two ends of the capacitor C5 are respectively connected to the positive input end and the output end of the fourth operational amplifier AD8065; the output end of the fourth operational amplifier AD8065 is connected to the output end of the advanced phase shift module; The forward zero-crossing detection module is used to detect the signal zero-crossing point to achieve the purpose of synchronous rectification; and a hysteresis comparison circuit is used to eliminate jitter; the two ends of the resistor R13 are respectively connected to the input end of the forward zero-crossing detection module and the positive input end of the first comparator TLV3502, the two ends of the resistor R14 are respectively connected to the reverse input end of the first comparator TLV3502 and the ground, and the two ends of the resistor R15 are respectively connected to the positive input end of the first comparator TLV3502 and the output end of the first comparator TLV3502; the output end of the first comparator TLV3502 is connected to the output end of the forward zero-crossing detection module; The forward integration module is used to produce a sawtooth wave; the two ends of the resistor R16 are respectively connected to the -5V voltage regulator and the reverse input end of the fifth operational amplifier AD8066, the two ends of the capacitor C6 are respectively connected to the reverse input end of the fifth operational amplifier AD8066 and the output end of the fifth operational amplifier AD8066, the drain of the seventh MOSFET switch tube is connected to the reverse input end of the fifth operational amplifier AD8066, the source of the seventh MOSFET switch tube is connected to the output end of the fifth operational amplifier AD8066, and the gate of the seventh MOSFET switch tube is connected to the input end of the forward integration module; the forward input end of the fifth operational amplifier AD8066 is connected to the ground, and the output end of the fifth operational amplifier AD8066 is connected to the output end of the forward integration module; The forward waveform correction circuit is used to correct the amplitude of the sawtooth waveform; the two ends of the resistor R17 are respectively connected to the input end of the forward waveform correction circuit and the positive input end of the sixth operational amplifier AD8066, the two ends of the resistor R18 are respectively connected to the positive input end of the sixth operational amplifier AD8066 and the output end of the sixth operational amplifier AD8066, the reverse input end of the sixth operational amplifier AD8066 is connected to the ground; the output end of the sixth operational amplifier AD8066 is connected to the output end of the forward waveform correction circuit; The forward control signal generating module is used to generate a gate signal for controlling the on and off of the fifth switch tube; a hysteresis comparison circuit is used to eliminate jitter; the two ends of the resistor R19 are respectively connected to the input end of the forward control signal generating module and the positive input end of the second comparator TLV3502, the two ends of the resistor R20 are respectively connected to the reverse input end of the second comparator TLV3502 and the ground, and the two ends of the resistor R21 are respectively connected to the positive input end of the second comparator TLV3502 and the output end of the second comparator TLV3502; the output end of the second comparator TLV3502 is connected to the output end of the forward control signal generating module; The reverse zero-crossing detection module is used to detect the zero-crossing point of the signal to achieve the purpose of synchronous rectification; a hysteresis comparison circuit is used to eliminate jitter; the two ends of the resistor R22 are respectively connected to the input end of the reverse zero-crossing detection module and the reverse input end of the third comparator TLV3502, the two ends of the resistor R23 are respectively connected to the positive input end of the third comparator TLV3502 and the ground, and the two ends of the resistor R24 ​​are respectively connected to the reverse input end of the third comparator TLV3502 and the output end of the first comparator TLV3502; the output end of the third comparator TLV3502 is connected to the output end of the reverse zero-crossing detection module; The reverse integration module is used to produce a sawtooth wave; the two ends of the resistor R25 are respectively connected to the -5V voltage regulator and the reverse input end of the seventh operational amplifier AD8066, the two ends of the capacitor C7 are respectively connected to the reverse input end of the seventh operational amplifier AD8066 and the output end of the seventh operational amplifier AD8066, the drain of the eighth MOSFET switch tube is connected to the reverse input end of the seventh operational amplifier AD8066, the source of the eighth MOSFET switch tube is connected to the output end of the seventh operational amplifier AD8066, and the gate of the eighth MOSFET switch tube is connected to the input end of the reverse integration module; the positive input end of the seventh operational amplifier AD8066 is connected to the ground, and the output end of the seventh operational amplifier AD8066 is connected to the output end of the reverse integration module; The reverse waveform correction module is used to correct the amplitude of the sawtooth waveform; the two ends of the resistor R26 are respectively connected to the input end of the reverse waveform correction module and the positive input end of the eighth operational amplifier AD8066, the two ends of the resistor R27 are respectively connected to the positive input end of the eighth operational amplifier AD8066 and the output end of the eighth operational amplifier AD8066, the reverse input end of the eighth operational amplifier AD8066 is connected to the ground; the output end of the eighth operational amplifier AD8066 is connected to the output end of the reverse waveform correction module; The reverse control signal generating module is used to generate a gate signal for controlling the on and off of the sixth switch tube; a hysteresis comparison circuit is used to eliminate jitter; the two ends of the resistor R28 are respectively connected to the input end of the reverse control signal generating module and the positive input end of the fourth comparator TLV3502, the two ends of the resistor R29 are respectively connected to the reverse input end of the fourth comparator TLV3502 and the ground, the two ends of the resistor 30 are respectively connected to the positive input end of the fourth comparator TLV3502 and the output end of the fourth comparator TLV3502; the output end of the fourth comparator TLV3502 is connected to the output end of the reverse control signal generating module.

9. The wireless power information simultaneous transmission device according to claim 1, characterized in that: The signal transmission circuit (8) processes the signal output by the current transformer (7) and then outputs a signal for controlling the fifth switch tube S5 and the sixth switch tube S6 in the semi-bridgeless active rectification circuit (3) to turn on and off, so that not only synchronous rectification can be achieved on the secondary side, but also information can be sent to the primary side by controlling the microcontroller MCU in the signal transmission circuit (8); the secondary side is one side of the semi-bridgeless active rectification circuit, that is, the power receiving end of the wireless transmission system, and has no physical connection with the primary side; the current transformer (7) comprises an iron core, a main winding and a secondary winding, the main winding and the secondary winding are wound on the iron core, when the measured current passes through the main winding of the transformer, a secondary current proportional to the main current is induced in the secondary winding, and by detecting the secondary current, the current in the main circuit can be indirectly measured; wherein the two ends of the main winding are connected to the secondary semi-bridgeless active rectification circuit (3), and the secondary winding is connected to the input end of the signal transmission circuit.

10. A method for simultaneously transmitting wireless power information according to any one of claims 1 to 5, characterized in that: The method comprises the following steps: (a) A DC regulated power supply (1) wirelessly transmits electric energy to a load (5) through a full-bridge inverter circuit (2), a semi-bridgeless active rectifier circuit (3) and a magnetic coupling resonant network (4), and a wireless power transmission system is constructed; (b) a current transformer (7) collects a current signal of the semi-bridgeless active rectifier circuit (3), and implements synchronous rectification of the MOSFET switch tube in the semi-bridgeless active rectifier circuit (3) through the signal sending circuit (8), so as to improve the efficiency of the wireless power transmission system; (c) the microcontroller MCU in the signal transmission circuit (8) modulates the signal in the signal transmission circuit (8), controls the duty cycle of the output PWM signal, changes the conduction duty cycle of the two MOSFET switch tubes in the semi-bridgeless active rectifier circuit (3) within the operating frequency cycle, and completes the transmission of information on the secondary side; (d) The signal receiving circuit (6) is connected to the full-bridge inverter circuit (2) and receives information transmitted from the secondary side to the primary side by detecting the current in the full-bridge inverter circuit (2), thereby realizing synchronous transmission of power information.

Images