Ultra-wideband double-compensation phase shifter

Abstract

The invention discloses an ultra-wideband double-compensation type phase shifter, which comprises two one-to-two switches, and a reference state branch and a phase shift state branch which are connected between the two one-to-two switches, the reference state branch comprises a magnetic coupling inductor L1, a capacitor C2, a capacitor C3 and two compensation capacitors C1, the capacitor C2 is connected from the center of the magnetic coupling inductor L1 to the ground, and the capacitor C3 is connected from the center of the magnetic coupling inductor L1 to the ground. The capacitor C3 is connected with the magnetic coupling inductor L1 in parallel to form a magnetic coupling all-pass network, the two compensation capacitors C1 are symmetrically connected to the two sides of the magnetic coupling all-pass network in series, the phase shift state branch comprises an inductance type all-pass network and two compensation inductors L4, the inductance type all-pass network comprises an inductor L2, an inductor L3 and two capacitors C4, the inductor L3 is connected to the two capacitors C4 in series in parallel, and the compensation inductors L4 are connected to the two capacitors C4 in parallel. The inductor L2 is connected to the ground at the center of the two capacitors C4 connected in series, the two compensation inductors L4 are symmetrically connected to the two sides of the inductance type all-pass network in series, the compensation capacitors C1 and the compensation inductors L4 can compensate the phase, the phase frequency response change rate is slowed down, and phase shifting under the extremely wide bandwidth is achieved.

Description

Technical Field

[0001] The invention relates to the field of monolithic microwave integrated circuits, and in particular to an ultra-wideband double-compensation phase shifter. Background Art

[0002] With the surge in demand for ultra-wideband communications in modern communication systems, ultra-wideband phased array systems have been widely studied. Ultra-wideband phased array systems can provide enhanced flexibility, efficiency, and performance, and have become one of the key technologies for ultra-wideband communications. Phase shifters are key components in phased array systems, and their bandwidth directly limits whether phased array systems can develop towards ultra-wideband applications. Therefore, the study of ultra-wideband phase shifters is of vital importance.

[0003] In order to expand the bandwidth, a variety of novel phase-shifting topology networks have been proposed, such as high-lowpass network (HLN), all-pass network (APNs) and magnetically coupled all-pass network (MCAPN). Among them, the phase shift of HLN changes linearly within a certain frequency range, but the signal is greatly affected by dispersion and the bandwidth is limited; to alleviate the above phenomenon, the proposed APNs all-pass network structure can theoretically achieve full-band phase shifting, but in practical applications, it is still affected by parasitic factors, and dispersion will still seriously limit the bandwidth; MCAPN weakens the influence of parasitics through inductive coupling and achieves phase shifting with a wider bandwidth, but dispersion still exists in this structure, and ideal full-band phase shifting cannot be achieved. Therefore, in order to alleviate the current problem of full-band phase shifting, the bandwidth needs to be further expanded. Summary of the invention

[0004] The main technical problem solved by the present invention is to provide an ultra-wideband double-compensation phase shifter, further expand the bandwidth of the phase shifter, and realize phase shifting in a wider frequency band.

[0005] In order to solve the above technical problems, a technical solution adopted by the present invention is: to provide an ultra-wideband dual-compensation phase shifter, including: two one-to-two switches and a reference state branch and a phase-shift state branch connected between the two one-to-two switches, the two one-to-two switches select one of the reference state branch and the phase-shift state branch as the flow network of the radio frequency signal through a control signal, the reference state branch includes a magnetic coupling inductor L1, a capacitor C2, a capacitor C3 and two compensation capacitors C1, the capacitor C2 is connected to the ground from the center of the magnetic coupling inductor L1, the capacitor C3 is connected in parallel to the magnetic coupling inductor L1, and the magnetic coupling full branch is formed. The invention relates to a magnetic coupling all-pass network, wherein two compensation capacitors C1 are symmetrically connected in series on both sides of the magnetic coupling all-pass network to form a capacitor compensation type - magnetic coupling capacitor all-pass network (C-MCAPN), the phase shift state branch includes an inductor type all-pass network and two compensation inductors L4, the inductor type all-pass network includes an inductor L2, an inductor L3 and two capacitors C4, the inductor L3 is connected in parallel to two series C4 capacitors, the inductor L2 is connected to the ground at the center of the two series capacitors C4, and the two compensation inductors L4 are symmetrically connected in series on both sides of the inductor type all-pass network to form an inductor compensation type - inductor all-pass network (L-LAPN).

[0006] In a preferred embodiment of the present invention, the capacitor compensation type-magnetic coupling capacitor all-pass network is a symmetrical network composed of passive devices, and the RF signal flows into the compensation capacitor C1 on one side, flows through the magnetic coupling all-pass network, and then flows out from the symmetrical compensation capacitor C1.

[0007] In a preferred embodiment of the present invention, the inductor compensation type-inductor all-pass network is a symmetrical network composed of passive devices, and the RF signal flows into the compensation inductor L4 on one side, flows through the inductor type all-pass network, and then flows out from the symmetrical compensation inductor L4.

[0008] In a preferred embodiment of the present invention, the one-to-two switch includes a switch tube M1, a switch tube M2, a switch tube M3 and a switch tube M4. The switch tube M1 is connected in series with the switch tube M2, and the radio frequency signal is input or output from the series center of the switch tube M1 and the switch tube M2. The switch tube M1 and the switch tube M3 are connected in parallel to form a first radio frequency path, and the other end of the switch tube M3 is connected in parallel to the ground. The switch tube M2 and the switch tube M4 are connected in parallel to form a second radio frequency path, and the other end of the switch tube M4 is connected in parallel to the ground.

[0009] In a preferred embodiment of the present invention, it also includes a first control signal input terminal and a second control signal input terminal, the first control signal input terminal is respectively connected to the control terminals of the switch tube M2 and the switch tube M3, and the second control signal input terminal is respectively connected to the control terminals of the switch tube M1 and the switch tube M4.

[0010] In a preferred embodiment of the present invention, when the switch tube M1 and the switch tube M4 are turned on, the switch tube M2 and the switch tube M3 are turned off, and the RF signal flows to the reference state branch; when the switch tube M2 and the switch tube M3 are turned on, the switch tube M1 and the switch tube M4 are turned off, and the RF signal flows to the phase shift state branch.

[0011] In a preferred embodiment of the present invention, the capacitor compensation type-magnetic coupling capacitor all-pass network compensates the phase of the reference state through the compensation capacitor C1, and tunes the frequency response change rate of the reference state phase. The larger the capacitance, the smaller the frequency response change rate.

[0012] In a preferred embodiment of the present invention, the inductor compensation type-inductor full-pass network compensates the phase of the phase-shift state by compensating the inductor L4, and tunes the frequency response change rate of the phase of the phase-shift state. The larger the inductance, the smaller the phase change rate.

[0013] The beneficial effect of the present invention is that: in an ultra-wideband dual-compensation phase shifter pointed out by the present invention, the compensation capacitor C1 in the reference state branch and the compensation inductor L4 in the phase-shifting state branch can both compensate for the phase, have a dual compensation effect, greatly slow down the phase frequency response change rate, and realize phase shifting under extremely wide bandwidth. BRIEF DESCRIPTION OF THE DRAWINGS

[0014] In order to more clearly illustrate the technical solutions in the embodiments of the present invention, the following briefly introduces the drawings required for describing the embodiments. Obviously, the drawings described below are only some embodiments of the present invention. For those skilled in the art, other drawings can be obtained based on these drawings without creative work, among which:

[0015] Figure 1 It is a schematic diagram of a preferred embodiment of an ultra-wideband dual-compensation phase shifter of the present invention;

[0016] Figure 2 yes Figure 1 Schematic diagram of the one-to-two switch;

[0017] Figure 3 This is a diagram showing the effect of the reference-state C-MCAPN compensation capacitor of an ultra-wideband dual-compensation phase shifter of the present invention on the compensation of the phase change rate;

[0018] Figure 4 This is a diagram showing the effect of the phase change rate compensation of the L-LAPN compensation inductor in the phase shift state of an ultra-wideband dual-compensation phase shifter of the present invention;

[0019] Figure 5 A comparison diagram of the phase change rate between a dual compensation structure of an ultra-wideband dual compensation type phase shifter and a non-dual compensation structure of the present invention;

[0020] Figure 6A diagram showing the phase shifting implementation result of an ultra-wideband dual-compensation phase shifter according to the present invention;

[0021] Figure 7 This is a diagram showing the S-parameter implementation results of an ultra-wideband dual-compensation phase shifter of the present invention. DETAILED DESCRIPTION

[0022] The technical solutions in the embodiments of the present invention are described clearly and completely below. Obviously, the described embodiments are only part of the embodiments of the present invention, not all of the embodiments. Based on the embodiments of the present invention, all other embodiments obtained by ordinary technicians in this field without creative work are within the scope of protection of the present invention.

[0023] See also Figure 1 to Figure 7 , the embodiment of the present invention includes:

[0024] like Figure 1 The ultra-wideband dual-compensation phase shifter shown in the figure includes: two one-to-two switches and a reference state branch and a phase-shift state branch connected between the two one-to-two switches. The two one-to-two switches select one of the reference state branch and the phase-shift state branch as the flow network of the radio frequency signal through a control signal, such as Figure 2 As shown, the one-to-two switch includes switch tube M1, switch tube M2, switch tube M3 and switch tube M4. Switch tube M1 is connected in series with switch tube M2. The RF signal is input or output from the center of the series connection of switch tube M1 and switch tube M2. Switch tube M1 is connected in parallel with switch tube M3 to form a first RF path. The other end of switch tube M3 is connected in parallel to the ground. The first RF path passes through Figure 2 The RF1 port output in.

[0025] The switch tube M2 is connected in parallel with the switch tube M4 to form a second RF path. The other end of the switch tube M4 is connected in parallel to the ground. The second RF path passes through Figure 2 In the present embodiment, the control signal is inputted through the first control signal input terminal Vctr1 and the second control signal input terminal Vctr2 respectively. The first control signal input terminal Vctr1 is connected to the control terminal of the switch tube M2 and the switch tube M3 respectively. The second control signal input terminal Vctr2 is connected to the control terminal of the switch tube M1 and the switch tube M4 respectively. The first power control signal is inputted through the first control signal input terminal Vctr1, and the second power control signal is inputted through the second control signal input terminal Vctr2. In the present embodiment, the first power control signal and the second power control signal are complementary levels.

[0026] When the switch tubes M1 and M4 are turned on, the switch tubes M2 and M3 are turned off, and the RF signal flows to the reference state branch, such as Figure 1As shown, the reference state branch includes a magnetic coupling inductor L1, a capacitor C2, a capacitor C3 and two compensation capacitors C1. The capacitor C2 is connected from the center of the magnetic coupling inductor L1 to the ground. The capacitor C3 is connected in parallel with the magnetic coupling inductor L1 to form a magnetic coupling all-pass network. The two compensation capacitors C1 are symmetrically connected in series on both sides of the magnetic coupling all-pass network to form a capacitor compensation type - magnetic coupling capacitor all-pass network (C-MCAPN). The capacitor compensation type - magnetic coupling capacitor all-pass network is a symmetrical network composed of passive devices. The RF signal flows into the compensation capacitor C1 on one side, flows through the magnetic coupling all-pass network, and then flows out from the symmetrical compensation capacitor C1.

[0027] In this embodiment, the capacitor compensation type - magnetically coupled capacitor all-pass network compensates the phase of the reference state through the compensation capacitor C1, tunes the frequency response change rate of the reference state phase, especially tunes the low frequency, and the larger the capacitance, the smaller the frequency response change rate.

[0028] When the switch tubes M2 and M3 are turned on, the switch tubes M1 and M4 are turned off, and the RF signal flows to the phase-shifted branch, such as Figure 1 As shown, the phase-shifted branch includes an inductive all-pass network and two compensation inductors L4. The inductive all-pass network includes an inductor L2, an inductor L3 and two capacitors C4. The inductor L3 is connected in parallel to two series-connected C4 capacitors. The inductor L2 is connected to the ground at the center of the two series-connected capacitors C4. The two compensation inductors L4 are symmetrically connected in series on both sides of the inductive all-pass network to form an inductive compensation-inductor all-pass network (L-LAPN). The inductive compensation-inductor all-pass network is a symmetrical network composed of passive devices. The RF signal flows into the compensation inductor L4 on one side, flows through the inductive all-pass network, and then flows out from the symmetrical compensation inductor L4.

[0029] In this embodiment, the inductor compensation type-inductor full-pass network compensates the phase of the phase-shift state by compensating the inductor L4, and tunes the frequency response change rate of the phase of the phase-shift state. The larger the inductance, the smaller the phase change rate.

[0030] The relevant derivation is as follows:

[0031] Reference state phase:

[0032]

[0033] M=k*L1

[0034] Among them, C1, C2, and C3 are the capacitance values ​​of the corresponding capacitor devices in the reference state, L1 is the inductance value of the magnetic coupling inductor in the reference state, k is the magnetic coupling coefficient, ω is the angular frequency, and Z0 is the characteristic impedance.

[0035] Phase shift state:

[0036]

[0037] Wherein, C4 is the capacitance value of the corresponding capacitor device in the phase-shift state, L2, L3, L4 are the inductance values ​​of the corresponding inductor devices in the phase-shift state, ω is the angular frequency, and Z0 is the characteristic impedance.

[0038] By analyzing the phases of the reference state and the phase-shifted state, the phase shift amount that can be achieved by this structure is the phase difference between the phase-shifted state and the reference state, that is:

[0039]

[0040] The first-order derivative of the phase shifter is:

[0041]

[0042] After taking the first-order derivative of the phase shift, it can be seen that the compensation capacitor C1 in the reference state capacitor compensation type-magnetically coupled capacitor all-pass network (C-MCAPN) plays a tuning role in the frequency response change rate of the phase, especially at low frequencies. The larger the capacitance, the smaller the phase change rate. The compensation effect of the frequency response change rate of the phase is as follows: Figure 3 shown.

[0043] In addition, after taking the first-order derivative of the phase shift amount, it can be seen that the compensation inductor L4 in the phase-shift inductor compensation type-inductor all-pass network (L-LAPN) plays a tuning role in the frequency response change rate of the phase. The larger the inductance, the smaller the phase change rate. The compensation effect of the frequency response change rate of the phase is as follows: Figure 4 shown.

[0044] The double compensation effect of phase can be achieved by using the compensation capacitor in the reference state branch and the compensation inductor in the phase shift state branch, such as Figure 5 As shown in the figure, compared with the phase change rate of the double compensation structure and the non-double compensation structure, the double compensation structure greatly slows down the phase frequency response change rate, making the phase frequency response change rate closer to zero, thus achieving an extremely wide broadband down-phase shift.

[0045] like Figure 6 As shown, according to Figure 1 The schematic diagram adopts a double-compensation phase-shifting structure, which achieves a 180° phase shift at a relative bandwidth of 152.9% at the center 3.4GHz, with an in-band fluctuation of ±7.5°, achieving phase shift in an extremely wideband range.

[0046] like Figure 7 As shown, the S parameter performance of the phase shifter in this embodiment is also good within the band, S21 is less than -4.2dB, and the return loss S11 is less than -11.5dB, wherein Path1 corresponds to the reference state S parameter performance, and Path2 corresponds to the phase shift state S parameter performance.

[0047] In summary, the ultra-wideband dual-compensation phase shifter pointed out in the present invention has a dual compensation effect, greatly slows down the phase frequency response change rate, realizes phase shifting under extremely wide bandwidth, is conducive to solving the problem of bandwidth being limited by dispersion, and further expands the bandwidth of the phase shifter.

[0048] The above are only embodiments of the present invention, and are not intended to limit the patent scope of the present invention. Any equivalent structure or equivalent process transformation made using the contents of the present invention specification, or directly or indirectly applied in other related technical fields, are also included in the patent protection scope of the present invention.

Claims

1. An ultra-wideband dual-compensation phase shifter, characterized in that: include: Two one-to-two switches and a reference state branch and a phase-shift state branch connected between the two one-to-two switches. The two one-to-two switches select one of the reference state branch and the phase-shift state branch as a flow network for radio frequency signals through control signals. The reference state branch includes a magnetic coupling inductor L1, a capacitor C2, a capacitor C3 and two compensation capacitors C1. The capacitor C2 is connected from the center of the magnetic coupling inductor L1 to the ground. The capacitor C3 is connected in parallel with the magnetic coupling inductor L1 to form a magnetic coupling full-pass network. The two compensation capacitors C1 Symmetrically connected in series on both sides of the magnetically coupled all-pass network to form a capacitor compensation type-magnetically coupled capacitor all-pass network, the phase-shifted state branch includes an inductor type all-pass network and two compensation inductors L4, the inductor type all-pass network includes an inductor L2, an inductor L3 and two capacitors C4, the inductor L3 is connected in parallel to two series-connected C4 capacitors, the inductor L2 is connected to the ground at the center of the two series-connected capacitors C4, and the two compensation inductors L4 are symmetrically connected in series on both sides of the inductor type all-pass network to form an inductor compensation type-inductor all-pass network.

2. The ultra-wideband dual-compensation phase shifter according to claim 1, characterized in that: The capacitor compensation type-magnetic coupling capacitor all-pass network is a symmetrical network composed of passive devices. The radio frequency signal flows into the compensation capacitor C1 on one side, flows through the magnetic coupling all-pass network, and then flows out from the symmetrical compensation capacitor C1.

3. The ultra-wideband dual-compensation phase shifter according to claim 1, characterized in that: The inductor compensation type-inductor full-pass network is a symmetrical network composed of passive devices. The radio frequency signal flows in from the compensation inductor L4 on one side, flows through the inductor type full-pass network, and then flows out from the symmetrical compensation inductor L4.

4. The ultra-wideband dual-compensation phase shifter according to claim 1, characterized in that: The one-to-two switch includes a switch tube M1, a switch tube M2, a switch tube M3 and a switch tube M4. The switch tube M1 is connected in series with the switch tube M2, and a radio frequency signal is input or output from the center of the series connection of the switch tube M1 and the switch tube M2. The switch tube M1 and the switch tube M3 are connected in parallel to form a first radio frequency path, and the other end of the switch tube M3 is connected in parallel to the ground. The switch tube M2 and the switch tube M4 are connected in parallel to form a second radio frequency path, and the other end of the switch tube M4 is connected in parallel to the ground.

5. The ultra-wideband dual-compensation phase shifter according to claim 4, characterized in that: It also includes a first control signal input terminal and a second control signal input terminal, wherein the first control signal input terminal is connected to the control terminals of the switch tubes M2 and M3 respectively, and the second control signal input terminal is connected to the control terminals of the switch tubes M1 and M4 respectively.

6. The ultra-wideband dual-compensation phase shifter according to claim 4, characterized in that: When the switch tubes M1 and M4 are turned on, the switch tubes M2 and M3 are turned off, and the RF signal flows to the reference state branch; when the switch tubes M2 and M3 are turned on, the switch tubes M1 and M4 are turned off, and the RF signal flows to the phase shift state branch.

7. The ultra-wideband dual-compensation phase shifter according to claim 1, characterized in that: The capacitor compensation type-magnetic coupling capacitor all-pass network compensates the phase of the reference state through the compensation capacitor C1, and tunes the frequency response change rate of the reference state phase.

8. The ultra-wideband dual-compensation phase shifter according to claim 1, characterized in that: The inductor compensation type-inductor full-pass network compensates the phase of the phase-shift state by means of the compensation inductor L4, and tunes the frequency response change rate of the phase of the phase-shift state.

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