A DC voltage stabilizing circuit and DC-DC converter

Abstract

The present application relates to the technical field of trans-inductor voltage regulators and discloses a DC voltage stabilization circuit and a DC-DC converter. The application introduces the secondary side winding in series into the main power loop, and adds a flying capacitor while connecting the compensation inductor and the center point of the half-bridge. When the inductor current of each phase reaches a stable equilibrium, the DC components between the secondary side winding and the primary side winding cancel each other out in equal magnitude and opposite direction, eliminating the risk of core saturation caused by unidirectional magnetic flux on the primary side of traditional trans-inductor voltage regulators, and greatly simplifying the dependence on high-saturation magnetic core materials. In addition, the charge and discharge balance characteristics and dynamic voltage balancing mechanism of the flying capacitor effectively overcome the problem that the secondary winding current path is easily affected by the difference in loop impedance. On the basis of retaining the inherent fast transient response characteristics of the trans-inductor voltage regulator, the saturation flux design is simplified, which not only reduces the core volume and design cost, but also improves the system robustness in high current scenarios.

Description

Technical Field

[0001] The present invention relates to the technical field of trans-inductor voltage regulators, and in particular to a DC voltage stabilization circuit and a DC-DC converter. Background Art

[0002] As the computing power of high-performance computing chips such as CPUs and GPUs increases, their power supply requirements have gradually shifted to high-density scenarios, such as 48V medium-voltage input and 1V / hundreds of amperes low-voltage, high-current output. The instantaneous switching rate of processor loads can reach 1000 amperes per microsecond, placing almost stringent demands on the dynamic response capability and output voltage stability of the power supply. In this context, traditional multi-phase buck regulators, limited by their complex current sharing control and low response bandwidth, are difficult to adapt to high-power density scenarios. However, trans-inductor voltage regulators (TLVRs), with their simple multi-phase coupling structure, efficient interleaved drive capability, and fast transient response characteristics, have gradually become the mainstream solution for meeting the power supply challenges of these new chips.

[0003] However, in actual applications, the secondary-side winding across the inductor regulator frame does not participate in power transmission, and the primary-side winding must independently carry the entire output current. Its DC component will directly form a high-intensity unidirectional bias flux in the inductor core, forcing the core material to meet extremely high saturation flux density requirements. To avoid magnetic saturation, expensive low-loss, high-saturation cores must be selected during design, or the core volume must be significantly increased. This not only limits the improvement of power density, but also increases manufacturing costs and the difficulty of thermal management. In addition, because the secondary winding is only used to adjust the dynamic coupling characteristics, its loop lacks a current balancing mechanism, and the multi-phase branches are easily affected by parameter deviations, further weakening the system reliability. This structural defect directly restricts the practical application of TLVR in ultra-high step-down ratio and ultra-high current scenarios. Therefore, the existing DC regulators have complex design requirements for the saturation flux of the coupled inductor and high design costs. Summary of the Invention

[0004] In order to provide a basic understanding of some aspects of the disclosed embodiments, a brief summary is given below. The summary is not an extensive review, nor is it intended to identify key / critical elements or delineate the scope of protection of these embodiments, but rather serves as a prelude to the detailed description that follows.

[0005] In view of the above-mentioned shortcomings of the prior art, the present invention discloses a DC voltage stabilizing circuit and a DC-DC converter to simplify the saturation flux design.

[0006] The present invention provides a DC voltage stabilization circuit, comprising: a multi-phase output module, comprising half-bridge units connected in sequence; a flying capacitor corresponding to a pre-stage unit, which is arranged at the center point of the half-bridge of the pre-stage unit, wherein the half-bridge unit in the last order is determined as the last order unit, and the half-bridge units other than the last order unit are respectively determined as pre-stage units; an inductor module, comprising a compensation inductor corresponding to a first order unit and coupling inductors corresponding to each of the subsequent units, wherein the center point of the half-bridge of the first order unit is connected to the DC input end of a load module in sequence through the compensation inductor and the secondary side windings of each of the coupling inductors, wherein the half-bridge unit in the first order is determined as the first order unit, and the half-bridge units other than the first order unit are respectively determined as subsequent units; and a load module, comprising an output load.

[0007] In an embodiment of the present application, the number of the multi-phase output modules includes one or more.

[0008] In one embodiment of the present application, if there are multiple multi-phase output modules, the input end of each of the multi-phase output modules is respectively connected to a DC power supply, and the output end of each of the multi-phase output modules is coupled to the DC input end of the load module through the inductor module.

[0009] In one embodiment of the present application, the half-bridge unit includes: a high-side switch tube, the drain of the high-side switch tube in the first unit is connected to a DC power supply, and the source of the high-side switch tube in the upper unit is connected to the drain of the high-side switch tube in the lower unit, wherein any two adjacent half-bridge units are sequentially determined as the upper unit and the lower unit; a low-side switch tube, the drain of the low-side switch tube in the front unit is connected to the source of the high-side switch tube in the front unit through the corresponding flying capacitor, and the drain of the low-side switch tube in the last unit is connected to the source of the high-side switch tube in the last unit.

[0010] In one embodiment of the present application, the drain of the low-side switching tube in the first unit is connected to the DC input end of the load module through the compensation inductor and the secondary side winding of each coupled inductor in sequence; the drain of the low-side switching tube in the rear unit is connected to the DC input end of the load module through the corresponding primary side winding.

[0011] In one embodiment of the present application, the load module includes: the output load, the positive electrode of the output load is connected to the DC input terminal of the load module; the output resistor, the first end of the output resistor is connected to the DC input terminal of the load module; and the output capacitor, the positive electrode of the output capacitor is connected to the DC input terminal of the load module through the capacitor and resistor.

[0012] In one embodiment of the present application, the driving signals output to each of the half-bridge units have the same signal frequency; the driving signals output to the upper unit and the driving signals output to the lower unit have complementary waveforms.

[0013] In one embodiment of the present application, the driving signals output to the high-side switching tubes in each half-bridge unit have the same duty cycle; the driving signals output to the corresponding low-side switching tubes of the upper unit and the driving signals output to the corresponding low-side switching tubes of the lower unit are complementary.

[0014] In one embodiment of the present application, in the same multi-phase output module, the switching tubes between the half-bridge units are staggered and turned on in a first cycle, wherein the first cycle is determined according to the number of half-bridge units in the multi-phase output module; the switching tubes between each multi-phase output module are staggered and turned on in a second cycle, wherein the second cycle is determined according to the number of the multi-phase output modules.

[0015] The present invention provides a DC-DC converter, comprising the DC voltage stabilizing circuit as described above.

[0016] Beneficial effects of the present invention:

[0017] By introducing the secondary winding in series into the main power circuit, adding a flying capacitor while connecting the compensation inductor and the center point of the half-bridge, the secondary winding and the primary winding jointly undertake the task of large current transmission, that is, when the inductor current of each phase reaches a stable balance, the DC components between the secondary winding and the primary winding cancel each other out in equal magnitude and opposite direction, thereby completely eliminating the risk of core saturation caused by the unidirectional magnetic flux on the primary side of the traditional trans-inductor regulator, greatly simplifying the dependence on high-saturation magnetic core materials, and the charge and discharge balance characteristics and dynamic voltage balancing mechanism of the flying capacitor effectively overcome the problem that the secondary winding current path is easily affected by the difference in loop impedance, and realize multi-phase current spontaneous equalization without the need for complex control algorithms. In this way, the present application simplifies the saturation flux design on the basis of retaining the inherent fast transient response characteristics of the trans-inductor regulator, which not only reduces the core volume and design cost, but also improves the system robustness in large current scenarios, providing an efficient and reliable solution for ultra-high step-down ratio and dynamic load power supply requirements. BRIEF DESCRIPTION OF THE DRAWINGS

[0018] Figure 1 It is a schematic diagram of the structure of a trans-inductor voltage regulator in this application;

[0019] Figure 2 It is a structural diagram of a DC voltage stabilizing circuit in this application;

[0020] Figure 3 It is a schematic diagram of the structure of a half-bridge unit in this application;

[0021] Figure 4 It is a schematic structural diagram of a zero DC bias trans-inductor regulator in this application;

[0022] Figure 5 This is a schematic diagram of the structure of a two-module eight-phase series capacitor-type zero DC bias trans-inductor regulator in this application;

[0023] Figure 6 This is a driving signal diagram corresponding to a two-module eight-phase series capacitor-type zero DC bias trans-inductor regulator in this application;

[0024] Figure 7 This is a simulation waveform diagram of a two-module eight-phase series capacitor-type zero DC bias trans-inductor regulator in this application;

[0025] Figure 8 It is a flow chart of a driving method of a DC voltage stabilizing circuit in this application. DETAILED DESCRIPTION

[0026] The following describes the embodiments of the present invention through specific examples. Those skilled in the art can easily understand other advantages and effects of the present invention from the content disclosed in this specification. The present invention can also be implemented or applied through different specific embodiments. The details in this specification can also be modified or changed based on different viewpoints and applications without departing from the spirit of the present invention. It should be noted that the following embodiments and sub-samples in the embodiments can be combined with each other unless there is a conflict.

[0027] It should be noted that the illustrations provided in the following embodiments are merely schematic illustrations of the basic concept of the present invention. Therefore, the illustrations only show components related to the present invention and are not drawn according to the number, shape, and size of components in actual implementation. In actual implementation, the type, quantity, and proportion of each component may be changed arbitrarily, and the component layout may also be more complex.

[0028] In the following description, numerous details are discussed to provide a more thorough explanation of the present application. However, it will be apparent to those skilled in the art that embodiments of the present invention may be practiced without these specific details. In other embodiments, well-known structures and electronic devices are shown in block diagram form rather than in detail to avoid obscuring the embodiments of the present invention.

[0029] The terms "first," "second," and the like in the specification and claims of this application and the accompanying drawings are used to distinguish similar items and are not necessarily used to describe a particular order or precedence. It should be understood that the terms used in this manner are interchangeable where appropriate for the embodiments of the present application described herein. In addition, the terms "including," "having," and any variations thereof are intended to cover non-exclusive inclusions.

[0030] Unless otherwise stated, the term "plurality" means two or more.

[0031] In this application, the character " / " indicates that the preceding and following objects are in an "or" relationship. For example, A / B means: A or B.

[0032] The term "and / or" describes an association between objects, indicating that three relationships can exist. For example, A and / or B means: A or B, or A and B.

[0033] Before further explaining the present application in detail, the nouns and terms involved in the present application are explained. The nouns and terms involved in the present application are subject to the following interpretations.

[0034] Trans-inductor regulators, such as Figure 1 As shown in Figure 1, each phase circuit uses the primary winding of a coupled inductor as the output filter inductor, while the secondary winding is connected in series with a compensation inductor to form an electrical coupling. However, in high step-down ratio applications, the trans-inductor regulator faces significant power loss. Furthermore, since the secondary winding of the coupled inductor does not carry power output, the high current output of the primary winding places extremely stringent requirements on the design of the coupled inductor's saturation flux.

[0035] Flying capacitor is a capacitor used in multi-level inverters and is also a circuit component used to step down, step up or improve power waveforms.

[0036] Combine Figure 2 As shown, the present application provides a DC voltage stabilization circuit, including a multi-phase output module 201 , an inductor module 202 and a load module 203 .

[0037] Combine Figure 3 As shown, the multi-phase output module 201 includes half-bridge units 2011 connected in sequence, wherein the first-order half-bridge unit is determined as the first unit, the half-bridge units other than the first unit are respectively determined as the subsequent units, the last-order half-bridge unit is determined as the last unit, and the half-bridge units other than the last unit are respectively determined as the front units.

[0038] In some embodiments, any two adjacent half-bridge units are sequentially determined as an upper unit and a lower unit.

[0039] The flying capacitor 20113 corresponding to the pre-unit is set at the center point of the half bridge of the pre-unit.

[0040] The inductor module 202 includes a compensation inductor 2021 corresponding to the first unit and a coupling inductor 2022 corresponding to each subsequent unit.

[0041] The center point of the half bridge of the first unit is connected to the DC input terminal of the load module 203 through the compensation inductor and the secondary windings of each coupled inductor in sequence.

[0042] The load module 203 includes an output load.

[0043] The DC voltage stabilization circuit provided by the present application is adopted. By introducing the secondary winding in series into the main power circuit, a flying capacitor is added while connecting the compensation inductor and the center point of the half-bridge, so that the secondary winding and the primary winding jointly bear the task of high current transmission. That is, when the inductor current of each phase reaches a stable equilibrium, the DC components between the secondary winding and the primary winding cancel each other out in equal magnitude and opposite direction, thereby completely eliminating the risk of core saturation caused by the unidirectional magnetic flux on the primary side of the traditional trans-inductor voltage regulator, greatly simplifying the dependence on high-saturation magnetic core materials. In addition, the charge and discharge balance characteristics and dynamic voltage balancing mechanism of the flying capacitor effectively overcome the problem that the secondary winding current path is easily affected by the difference in loop impedance, and realize multi-phase current spontaneous current sharing without the need for complex control algorithms. In this way, the present application simplifies the saturation flux design while retaining the inherent fast transient response characteristics of the trans-inductor voltage regulator, which not only reduces the core volume and design cost, but also improves the system robustness in high current scenarios, providing an efficient and reliable solution for ultra-high step-down ratio and dynamic load power supply requirements.

[0044] Combine Figure 4 As shown, the present application provides a zero DC bias trans-inductor regulator, including a topology module 204 , an inductor module 202 and a load module 203 .

[0045] The topology module 204 is composed of a multi-phase output module 201 and its corresponding inductor module 202, wherein the number of the multi-phase output modules 201 includes one or more, and the multi-phase output modules 201 are in a parallel relationship. The input ends of the multi-phase output modules 201 are all connected to a DC power supply, and the output ends of the multi-phase output modules 201 are coupled to the DC input ends of the load module 203 through the inductor module 202.

[0046] The multi-phase output module 201 includes half-bridge units 2011 connected in sequence.

[0047] Optionally, the driving signals output to each of the half-bridge units have the same signal frequency; the driving signal output to the upper unit and the driving signal output to the lower unit have complementary waveforms.

[0048] Optionally, in the same multi-phase output module, the switching tubes between the half-bridge units are staggered and turned on in a first cycle, wherein the first cycle is determined according to the number of half-bridge units in the multi-phase output module; the switching tubes between each multi-phase output module are staggered and turned on in a second cycle, wherein the second cycle is determined according to the number of the multi-phase output modules.

[0049] In some embodiments, each multi-phase output module 201 is configured to provide N-phase output, where N is the number of half-bridge units in the multi-phase output module.

[0050] The half-bridge unit 2011 includes a high-side switch tube 20111 and a low-side switch tube 20112, and the front unit also includes a flying capacitor 20113, wherein the drain of the high-side switch tube in the first unit is connected to a DC power supply, the source of the high-side switch tube in the upper unit is connected to the drain of the high-side switch tube in the lower unit, the drain of the low-side switch tube in the front unit is connected to the source of the high-side switch tube in the front unit through the corresponding flying capacitor, and the drain of the low-side switch tube in the last unit is connected to the source of the high-side switch tube in the last unit.

[0051] Optionally, the drive signals output to the high-side switch tubes in each half-bridge unit have the same duty cycle; the drive signals output to the corresponding low-side switch tubes of the upper unit and the drive signals output to the corresponding low-side switch tubes of the lower unit are complementary.

[0052] In the first unit, the drain of the high-side switch tube 20111 is connected to the DC power supply, the source of the high-side switch tube 20111 is connected to the drain of the low-side switch tube 20112 through the flying capacitor 20113, the drain of the low-side switch tube 20112 is connected to the first end of the compensation inductor 2021, and the source of the low-side switch tube 20112 is grounded.

[0053] In the preamplifier unit, the drain of the high-side switch tube 20111 is connected to the center point of the half bridge of the upper unit, the source of the high-side switch tube 20111 is connected to the drain of the low-side switch tube 20112 through the flying capacitor 20113, and the source of the low-side switch tube 20112 is grounded.

[0054] In the post-unit, the drain of the low-side switch tube 20112 is connected to the same-named end of the primary-side winding.

[0055] In the last unit, the drain of the high-side switch tube 20111 is connected to the center point of the half bridge of the upper unit, the source of the high-side switch tube 20111 is connected to the drain of the low-side switch tube 20112, and the source of the low-side switch tube 20112 is grounded.

[0056] The inductor module 202 includes a compensation inductor 2021 corresponding to each first-stage unit and a coupling inductor 2022 corresponding to each subsequent unit, wherein the drain of the low-side switch tube in the first-stage unit is connected to the DC input end of the load module through the compensation inductor and the secondary side winding of each coupling inductor in sequence; the drain of the low-side switch tube in the subsequent unit is connected to the DC input end of the load module through the corresponding primary side winding.

[0057] The second end of the compensation inductor 2021 is connected to the opposite-name end of the secondary winding corresponding to the second-order half-bridge switch.

[0058] In the coupled inductor 2022, the opposite-name ends of the primary-side winding are connected to the DC input terminal of the load module 203, the same-name ends of the secondary-side winding corresponding to the upper-level unit are connected to the opposite-name ends of the secondary-side winding corresponding to the lower-level unit, and the same-name ends of the secondary-side winding corresponding to the last unit are connected to the DC input terminal of the load module 203.

[0059] The load module 203 includes an output load 2031 , an output resistor 2032 , an output capacitor 2033 , and a capacitor-resistor 2034 .

[0060] The positive electrode of the output load 2031 is connected to the DC input terminal of the load module, and the negative electrode of the output load 2031 is grounded.

[0061] A first end of the output resistor 2032 is connected to the DC input end of the load module, and a second end of the output resistor 2032 is grounded.

[0062] The positive electrode of the output capacitor 2033 is connected to the DC input terminal of the load module through the capacitor resistor 2034, and the negative electrode of the output capacitor 2033 is grounded.

[0063] Combine Figure 5 As shown, the present application provides a two-module eight-phase series capacitor-type zero DC bias trans-inductor regulator, which uses two multi-phase output modules to form a topology module, and each multi-phase output module has four half-bridge units.

[0064] In some embodiments, the driving signal corresponding to the two-module eight-phase series capacitor zero DC bias trans-inductor regulator is as follows: Figure 6 As shown, the input voltage is set to 48V, the output voltage is 1V, the switching frequency is 500kHz, the excitation inductance of the coupled inductor is 200nH, the compensation inductance is 50nH, and a DC equivalent resistance is set for both windings of each coupled inductor.

[0065] In some embodiments, the simulation waveform of the two-module eight-phase series capacitor zero DC bias trans-inductor regulator is as follows: Figure 7 As shown, DRV is the driving signal corresponding to the half-bridge unit, i L is the output current corresponding to the half-bridge unit, i Lm is the excitation current flowing through the coupled inductor core, i0 is the coupling current after each multi-phase output module outputs, V C1 、V C2 、V c3 、V C5 、V C6 、V C7 are the capacitance voltage division of each flying capacitor, V0 is the load voltage of the load module 203; from the simulation waveform, it can be seen that the voltage division V C1 and V C5The flying capacitor voltage is three-quarters of the 48V input voltage, that is, 36V. C2 and V C6 The flying capacitor voltage is half of the 48V input voltage, that is, 24V. C3 and V C7 The input voltage is one-quarter of the 48V, or 12V. The four phase currents within a single module are mutually coupled. Although the equivalent DC resistance of the current paths for phases 1 and 5 is three times that of the other phases, the steady-state charge and discharge balance of the flying capacitors ensures balanced phase currents within the module, and the DC component of the coupled inductor's excitation current is canceled out. The total output current is the sum of the eight phase output currents. The interleaved parallel connection cancels out current ripple, reducing the total output current ripple. Furthermore, the voltage divider effect of the flying capacitors doubles the duty cycle of the high-side switch in each phase compared to a traditional buck converter circuit, reducing the voltage stress on the switch.

[0066] Combine Figure 8 As shown, the present application provides a driving method for the above-mentioned DC voltage stabilizing circuit, comprising:

[0067] Step S801, obtaining a driving signal corresponding to each half-bridge unit;

[0068] The signal frequencies of the control signals are the same, and the waveforms of the drive signals corresponding to adjacent half-bridge units are complementary;

[0069] Step S802 : driving the corresponding half-bridge units respectively through the driving signals.

[0070] The driving method of the DC voltage regulator circuit provided by the present application is adopted. By introducing the secondary winding in series into the main power circuit, and adding a flying capacitor while connecting the compensation inductor and the center point of the half-bridge, the secondary winding and the primary winding jointly bear the task of high current transmission. That is, when the inductor current of each phase reaches a stable equilibrium, the DC components between the secondary winding and the primary winding cancel each other out in equal magnitude and opposite direction, thereby completely eliminating the risk of core saturation caused by the unidirectional magnetic flux on the primary side of the traditional trans-inductor regulator, greatly simplifying the dependence on high-saturation magnetic core materials. In addition, the charge and discharge balance characteristics and dynamic voltage balancing mechanism of the flying capacitor effectively overcome the problem that the secondary winding current path is easily affected by the difference in loop impedance, and realize multi-phase current spontaneous current sharing without the need for complex control algorithms. In this way, the present application simplifies the saturation flux design while retaining the inherent fast transient response characteristics of the trans-inductor regulator, which not only reduces the core volume and design cost, but also improves the system robustness in high current scenarios, providing an efficient and reliable solution for ultra-high step-down ratio and dynamic load power supply requirements.

[0071] Optionally, the method further includes: the driving signals output to the high-side switching tubes in each half-bridge unit have the same duty cycle; and the driving signal output to the upper unit and the driving signal output to the lower unit are complementary.

[0072] In some embodiments, when the DC voltage stabilization circuit is in steady state, the switch tube driving signals of all phases are complementary square waves of the same frequency, the driving signals of the high-side switch tubes all use the same duty cycle D, and the low-side switch tube driving signals between two adjacent half-bridge units are complementary.

[0073] Optionally, the method also includes: in the same multi-phase output module, the switching tubes between the half-bridge units are staggered and turned on in a first cycle, wherein the first cycle is determined according to the number of half-bridge units in the multi-phase output module; the switching tubes between each multi-phase output module are staggered and turned on in a second cycle, wherein the second cycle is determined according to the number of multi-phase output modules.

[0074] In some embodiments, in each multi-phase output module, the switch tubes between the half-bridge units are staggered at 360° / N, where N is the number of half-bridge units in the multi-phase output module.

[0075] In some embodiments, the switch tubes between each multi-phase output module are staggered at 360° / M, where M is the number of multi-phase output modules connected in parallel.

[0076] In some embodiments, the equivalent excitation inductance of the coupled inductor on the primary side winding is L m , the excitation current is i Lm , then i Lm =i pri -i sec ,i pri is the current of the primary winding, i sec is the current of the secondary winding, where the current of the secondary winding is equal, denoted as i L1 On the other hand, according to the charge and discharge balance of the flying capacitor, the relationship is obtained Where, is the DC component of each phase current, n∈[1,N-1]; when the DC voltage stabilization circuit is in steady state, the current direction of each phase current can be automatically balanced, and the excitation current of the nth phase on the primary side winding This achieves zero DC bias of the coupled inductor.

[0077] The present application also provides a DC-DC converter, comprising the above-mentioned DC voltage stabilizing circuit.

[0078] The above description and the accompanying drawings fully illustrate the embodiments of the present disclosure to enable those skilled in the art to practice them. Other embodiments may include structural, logical, electrical, process and other changes. The embodiments represent only possible variations. Unless expressly required, individual components and functions are optional, and the order of operations may vary. Parts and subsamples of some embodiments may be included in or replace parts and subsamples of other embodiments. Moreover, the terms used in this application are only used to describe the embodiments and are not used to limit the claims. As used in the description of the embodiments and claims, unless the context clearly indicates otherwise, the singular forms "a", "an" and "the" are intended to also include plural forms. Similarly, the term "and / or" as used in this application refers to any and all possible combinations of one or more associated listings. In addition, when used in this application, the term "comprise" and its variants "comprises" and / or comprising refer to the presence of a stated sub-sample, whole, step, operation, element, and / or component, but do not exclude the presence or addition of one or more other sub-samples, wholes, steps, operations, elements, components and / or groups of these. In the absence of further restrictions, an element defined by the statement "comprises a..." does not exclude the presence of other identical elements in the process, method or electronic device that includes the element. In this article, each embodiment may focus on the differences from other embodiments, and the same and similar parts between the various embodiments can be referenced to each other. For the methods, products, etc. disclosed in the embodiments, if they correspond to the method part disclosed in the embodiments, then the relevant parts can be found in the description of the method part.

[0079] Those skilled in the art will appreciate that the units and algorithm steps of each example described in conjunction with the embodiments disclosed herein can be implemented in electronic hardware, or a combination of computer software and electronic hardware. Whether these functions are performed in hardware or software may depend on the specific application and design constraints of the technical solution. Technicians can use different methods to implement the described functions for each specific application, but such implementation should not be considered to be beyond the scope of this application. Technicians can clearly understand that for the convenience and brevity of description, the specific working processes of the systems, devices and units described above can refer to the corresponding processes in the aforementioned method embodiments and will not be repeated here.

[0080] In the embodiments disclosed herein, the disclosed methods and products (including but not limited to devices, electronic devices, etc.) can be implemented in other ways. For example, the device embodiments described above are merely illustrative. For example, the division of units can be merely a logical functional division. In actual implementation, there may be other division methods, such as multiple units or components can be combined or integrated into another system, or some sub-samples can be ignored or not executed. In addition, the coupling or direct coupling or communication connection between each other shown or discussed can be through some interfaces, indirect coupling or communication connection of devices or units, and can be electrical, mechanical or other forms. The units described as separate components may or may not be physically separated, and the components shown as units may or may not be physical units, that is, they may be located in one place, or they may be distributed on multiple network units. Some or all of the units may be selected according to actual needs to implement this embodiment. In addition, the functional units in this application may be integrated into a processing unit, or each unit may exist physically separately, or two or more units may be integrated into one unit.

[0081] The flowcharts and block diagrams in the accompanying drawings show the possible architecture, functions and operations of the systems, methods and computer program products according to the present application. In this regard, each box in the flowchart or block diagram can represent a module, program segment or part of the code, and the module, program segment or part of the code contains one or more executable instructions for implementing the specified logical function. In some alternative implementations, the functions marked in the box can also occur in an order different from that marked in the accompanying drawings. For example, two consecutive boxes can actually be executed substantially in parallel, or they can sometimes be executed in the opposite order, which can depend on the functions involved. In the descriptions corresponding to the flowcharts and block diagrams in the accompanying drawings, the operations or steps corresponding to different boxes can also occur in an order different from that disclosed in the description, and sometimes there is no specific order between different operations or steps. For example, two consecutive operations or steps can actually be executed substantially in parallel, or they can sometimes be executed in the opposite order, which can depend on the functions involved. Each block in the block diagrams and / or flowcharts, and combinations of blocks in the block diagrams and / or flowcharts, may be implemented by a dedicated hardware-based system that performs the specified function or action, or may be implemented by a combination of dedicated hardware and computer instructions.

Claims

1. A DC voltage stabilizing circuit, characterized in that: include: A multi-phase output module comprising half-bridge units connected in sequence; The flying capacitor corresponding to the pre-unit is set at the center point of the half-bridge of the pre-unit, wherein the half-bridge unit in the last order is determined as the last unit, and the half-bridge units other than the last unit are respectively determined as pre-units; An inductor module, comprising a compensation inductor corresponding to a first unit and a coupling inductor corresponding to each subsequent unit, wherein the center point of the half-bridge of the first unit is connected to the DC input terminal of the load module in sequence through the compensation inductor and the secondary windings of each coupling inductor, wherein the first-order half-bridge unit is determined as the first unit, and the half-bridge units other than the first unit are respectively determined as subsequent units; The half-bridge unit includes a high-side switch tube, wherein the drain of the high-side switch tube in the first unit is connected to a DC power supply, and the source of the high-side switch tube in the upper unit is connected to the drain of the high-side switch tube in the lower unit, wherein any two adjacent half-bridge units are sequentially determined as the upper unit and the lower unit; a low-side switch tube, wherein the drain of the low-side switch tube in the front unit is connected to the source of the high-side switch tube in the front unit through a corresponding flying capacitor, and the drain of the low-side switch tube in the last unit is connected to the source of the high-side switch tube in the last unit; The drain of the low-side switch tube in the first unit is connected to the DC input end of the load module through the compensation inductor and the secondary side winding of each coupled inductor in sequence; the drain of the low-side switch tube in the rear unit is connected to the DC input end of the load module through the corresponding primary side winding; Load module, including output load.

2. The DC voltage stabilizing circuit according to claim 1, wherein: The number of the multi-phase output modules includes one or more.

3. The DC voltage stabilizing circuit according to claim 2, wherein: If there are multiple multi-phase output modules, the input end of each multi-phase output module is connected to a DC power supply, and the output end of each multi-phase output module is coupled to the DC input end of the load module through the inductor module.

4. The DC voltage stabilizing circuit according to claim 1, wherein: The load module includes: The output load, wherein the positive electrode of the output load is connected to the DC input terminal of the load module; an output resistor, wherein a first end of the output resistor is connected to the DC input end of the load module, and a second end of the output resistor is grounded; An output capacitor, wherein the positive electrode of the output capacitor is connected to the DC input terminal of the load module through a capacitor and a resistor, and the negative electrode of the output capacitor is grounded.

5. The DC voltage stabilizing circuit according to any one of claims 1 to 4, characterized in that: The driving signals output to each of the half-bridge units have the same signal frequency; The driving signal output to the upper unit and the driving signal output to the lower unit have complementary waveforms.

6. The DC voltage stabilizing circuit according to claim 5, characterized in that: The driving signals output to the high-side switching tubes in each half-bridge unit have the same duty cycle; The driving signal output to the low-side switch tube corresponding to the upper unit and the driving signal output to the low-side switch tube corresponding to the lower unit are complementary.

7. The DC voltage stabilizing circuit according to claim 5, characterized in that: In the same multi-phase output module, the switch tubes between the half-bridge units are staggeredly turned on in a first period, wherein the first period is determined according to the number of half-bridge units in the multi-phase output module; The switch tubes between the multi-phase output modules are alternately turned on in a second period, wherein the second period is determined according to the number of the multi-phase output modules.

8. A DC-DC converter, characterized in that: The method comprises the DC voltage stabilizing circuit according to any one of claims 1 to 7.

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