Rapid calculation method for equivalent circuit parameters of high-capacity alternating-current excitation motor

Abstract

The invention discloses a method for quickly calculating equivalent circuit parameters of a high-capacity alternating-current excitation motor, which belongs to the field of motor parameter calculation, and comprises the following steps of: dividing stator and rotor leakage inductance into stator and rotor slot leakage inductance, stator and rotor harmonic leakage inductance, stator and rotor end leakage inductance and stator and rotor tooth crest leakage inductance from the magnetic flux path and characteristics of the motor; respectively and accurately calculating the four parts of leakage inductance according to the path through which each magnetic flux passes; according to the method, information such as flux linkage and magnetic energy storage obtained from static field simulation is fully utilized to calculate motor parameters, all the motor parameters can be calculated only through three static field simulation, and compared with a conventional parameter calculation method based on a transient field, the parameter calculation efficiency of the type of motors can be improved; and the design period of the high-capacity alternating-current excitation motor can be shortened.

Description

Technical Field

[0001] The present invention belongs to the field of motor parameter calculation, and more specifically, relates to a method for quickly calculating equivalent circuit parameters of a large-capacity AC excited motor. Background Art

[0002] The equivalent circuit parameters of a large-capacity AC excited motor directly affect its power regulation range and response speed to the power grid. Therefore, the new power system puts forward higher requirements for the accurate design of the parameters of a large-capacity AC excited motor. At present, the parameter calculation methods mainly refer to synchronous motors of the same capacity, megawatt-level doubly-fed fans, or large-scale asynchronous motors. However, the operating conditions of large-capacity AC excited motors change frequently, the speed regulation range is wide, and the range of change in slot current is large, resulting in parameter changes of their equivalent circuit parameters within the variable speed range, so that conventional analytical algorithms or empirical formulas are difficult to accurately calculate the equivalent circuit parameters of large-capacity AC excited motors under all operating conditions.

[0003] Some existing finite element parameter calculation methods need to perform multiple transient simulations and go through a complex post-processing process to obtain accurate motor parameters, which greatly reduces the motor design efficiency; there are also some parameter calculation methods that separately calculate the stator and rotor leakage inductances, but these parameter calculation methods either ignore the calculation of harmonic leakage inductance or ignore the calculation of tooth tip leakage inductance. Among the above methods, whether it is the parameter calculation method that ignores slot leakage inductance or tooth tip leakage inductance, there are problems of insufficient calculation accuracy, and these methods cannot be applied to the occasions where harmonic leakage inductance and tooth tip leakage inductance need to be calculated simultaneously, and the versatility of such methods is insufficient; there are also some parameter calculation methods that first calculate the total leakage inductance, and then subtract the sum of slot leakage inductance, harmonic leakage inductance, and end leakage inductance from the total leakage inductance to obtain the tooth tip leakage inductance. This type of method calculates all the leakage inductance parameters, but the calculation accuracy of the tooth tip leakage inductance in this type of calculation method is affected by the calculation accuracy of other leakage inductance parameters. If the calculated value of the total leakage inductance is larger than the true value and the calculated values of other leakage inductances are smaller than the true value, this will cause the calculated value of the tooth tip leakage inductance to deviate more from the true value. Therefore, this type of method cannot meet the calculation accuracy requirements of the equivalent circuit parameters of large-capacity AC excited motors. Summary of the Invention

[0004] In view of the above defects or improvement requirements of the prior art, the present invention provides a method for quickly calculating equivalent circuit parameters of a large-capacity AC excited motor, which helps to improve the design efficiency and parameter accuracy of a large-capacity AC excited motor, and is beneficial to giving full play to the supporting role of a large-capacity AC excited motor in the new power system.

[0005] To achieve the above object, according to the first aspect of the present invention, there is provided a method for quickly calculating equivalent circuit parameters of a large-capacity AC excited motor, including:

[0006] S1. Divide the stator leakage inductance and rotor leakage inductance of the motor into slot leakage inductance, harmonic leakage inductance, tooth tip leakage inductance, and end leakage inductance; wherein, the equivalent circuit parameters of the motor include excitation inductance, stator leakage inductance, and rotor leakage inductance;

[0007] S2. Select the corresponding end leakage inductance calculation formula according to the end winding shape of the motor to calculate the end leakage inductance of the stator and rotor;

[0008] S3. Establish a first simulation model of the motor in finite element software, run the first simulation model under rated conditions using the static magnetic field simulation technology of the finite element software, and save the stator permeability and rotor permeability in the first simulation model, as well as the radial magnetic density entering the teeth of the stator and rotor;

[0009] S4. Calculate the excitation inductance, harmonic leakage inductance of the stator and rotor according to the radial magnetic density of the teeth of the stator and rotor;

[0010] S5. Establish a second simulation model of the motor in finite element software, set its stator permeability to the stator permeability in S3, set its stator three-phase currents I A 、I B 、I C , set its rotor permeability to infinitesimal, set the rotor current to 0, run the second simulation model using the static magnetic field simulation technology of the finite element software, save the magnetic energy storage in the stator slots and the magnetic energy storage in the air gap W ssl and W sgl , and calculate the stator slot leakage inductance and stator tooth tip leakage inductance L according to the formula ssl and L sgl ;

[0011] Establish a third simulation model of the motor in finite element software, set its rotor permeability to the rotor permeability in S3, set its rotor three-phase currents I U 、I V 、I W , set its stator permeability to infinitesimal, set the stator current to 0, run the third simulation model using the static magnetic field simulation technology of the finite element software, save the magnetic energy storage in the rotor slots and the magnetic energy storage in the air gap W rsl and W rgl , and calculate the rotor slot leakage inductance and rotor tooth tip leakage inductance L according to the formula rsl and L rgl .

[0012] According to the second aspect of the present invention, there is provided an electronic device, including: a computer-readable storage medium and a processor;

[0013] The computer-readable storage medium is used to store executable instructions;

[0014] The processor is configured to read the executable instructions stored in the computer-readable storage medium and execute the method described in the first aspect.

[0015] According to a third aspect of the present invention, there is provided a computer-readable storage medium storing computer instructions for causing a processor to execute the method described in the first aspect.

[0016] According to a fourth aspect of the present invention, there is provided a computer program product including a computer program or instructions, which when executed by a processor implement the method described in the first aspect.

[0017] Generally speaking, compared with the prior art by the above technical solution conceived by the present invention, the following beneficial effects can be achieved:

[0018] To solve the problems of low calculation efficiency and insufficient accuracy in the existing calculation method of equivalent circuit parameters of large-capacity AC excited motors, the present invention provides a method for quickly calculating equivalent circuit parameters of large-capacity AC excited motors. Starting from the flux path and characteristics of the motor, the stator and rotor leakage inductances are divided into stator and rotor slot leakage inductances, stator and rotor harmonic leakage inductances, stator and rotor end leakage inductances, and stator and rotor tooth-top leakage inductances. For each path through which the flux passes, the four parts of leakage inductances are accurately calculated. Considering that the slot leakage flux of the stator and rotor of the motor only passes through the stator and rotor slots and most of the tooth-top leakage flux only passes through the air gap, therefore, the energies in the stator and rotor slots of the motor and the energy in the air gap are calculated respectively, and then the stator and rotor slot leakage inductances and the stator and rotor tooth-top leakage inductances are obtained respectively; considering that both the harmonic flux linkage and the main flux linkage penetrate the stator and rotor teeth radially, therefore, based on the flux linkage method, the harmonic flux linkage and the main flux linkage penetrating into the iron core are calculated respectively, and then the stator and rotor harmonic leakage inductances and the excitation inductance are obtained respectively; considering that the current end leakage inductance calculation formula is relatively mature, therefore, an empirical formula for end leakage inductance that conforms to the end shape of the stator and rotor windings is selected to obtain the end leakage inductance, which has both high calculation accuracy and fast calculation speed; and, during the calculation of the above parameters, the frozen permeability function in the static field finite element simulation technology is adopted to ensure that the permeability during parameter calculation is consistent with the permeability of the required operating conditions, so that this method can consider the non-linear change of parameters caused by iron core saturation; compared with the conventional finite element parameter calculation method, only 3 static field finite element simulations are required to obtain all the inductance parameters of the equivalent circuit of the large-capacity AC excited motor and complete the extraction calculation of all leakage inductances, which greatly improves the parameter calculation efficiency of this type of motor and is beneficial to shortening the design cycle of large-capacity AC excited motors.

[0019] In summary, the method provided by the present invention calculates according to the specific paths and characteristics of each part of the magnetic flux. Therefore, the leakage inductances of each part of the stator and rotor can be accurately calculated, and it has higher accuracy compared with the existing parameter calculation methods. In addition, the present invention makes full use of the information such as magnetic flux linkage and magnetic energy storage obtained from the static field simulation to calculate the motor parameters. Only 3 static field simulations are required to calculate all the motor parameters. Compared with the conventional parameter calculation method based on the transient field, it can improve the efficiency of parameter acquisition. BRIEF DESCRIPTION OF THE DRAWINGS

[0020] Figure 1 is a schematic flow chart of a method for quickly calculating equivalent circuit parameters of a large-capacity AC excited motor provided by an embodiment of the present invention;

[0021] Figure 2 is a detailed inductance model of a large-capacity AC excited motor provided by an embodiment of the present invention;

[0022] Figure 3 is a magnetic field line distribution diagram when the stator slot leakage inductance and the stator tooth tip leakage inductance of an embodiment of the present invention are present. DETAILED DESCRIPTION OF THE EMBODIMENTS

[0023] In order to make the objectives, technical solutions and advantages of the present invention clearer, the present invention will be further described in detail below with reference to the accompanying drawings and embodiments. It should be understood that the specific embodiments described herein are only used to explain the present invention and are not used to limit the present invention. In addition, the technical features involved in the various embodiments of the present invention described below can be combined with each other as long as they do not conflict with each other.

[0024] An embodiment of the present invention provides a method for quickly calculating equivalent circuit parameters of a large-capacity AC excited motor, as Figure 1 shown, including:

[0025] S1, dividing the stator leakage inductance and the rotor leakage inductance of the motor into slot leakage inductance, harmonic leakage inductance, tooth tip leakage inductance and end leakage inductance; wherein, the equivalent circuit parameters of the motor include excitation inductance, stator leakage inductance and rotor leakage inductance.

[0026] Specifically, based on the equivalent circuit of a large-capacity AC excited motor, a detailed inductance model of a large-capacity AC excited motor is established: ignoring the stator and rotor resistances of the large-capacity AC excited motor, the stator leakage inductance and the rotor leakage inductance are respectively subdivided. The stator leakage inductance is divided into the slot leakage inductance, harmonic leakage inductance, tooth tip leakage inductance and end leakage inductance of the stator, and the rotor leakage inductance is similarly divided into the slot leakage inductance, harmonic leakage inductance, tooth tip leakage inductance and end leakage inductance of the rotor. The detailed inductance model is as Figure 2 shown.

[0027] Figure 2 In, U s , E 0 , Ur The ′ / s and ω represent the stator voltage, back electromotive force, rotor voltage referred to the stator side, and stator angular frequency respectively, and L se , L ssl , L shl and L sgl represent the stator end leakage inductance, stator slot leakage inductance, stator harmonic leakage inductance, and stator tooth-top leakage inductance respectively, and L m represents the excitation inductance, and L re ′, L rsl ′, L rhl ′ and L rgl ′ represent the rotor end leakage inductance, rotor slot leakage inductance, rotor harmonic leakage inductance, and rotor tooth-top leakage inductance referred to the stator side respectively. These referred values have the following relationships with the rotor leakage inductance parameters calculated in the present invention.

[0028]

[0029] where L′ represents Figure 2 the rotor leakage inductance value in w1 and K w2 represent the stator winding coefficient and rotor winding coefficient respectively, and N 1 and N 2 represent the number of series turns per phase of the stator and the number of series turns per phase of the rotor respectively.

[0030] S2, select the corresponding end leakage inductance calculation formula according to the end winding shape of the motor to calculate the end leakage inductance of the stator and rotor.

[0031] Specifically, use the analytical calculation formula to calculate the end leakage inductance of the stator and rotor of the large-capacity AC excited motor.

[0032] According to the end winding shape of the stator of the large-capacity AC excited motor, select the analytical calculation formula that conforms to the end shape of the motor. For example, for the double-layer lap winding or wave winding, the following calculation formula can be used:

[0033]

[0034] where, L se is the stator end leakage inductance, N 1 and K w1 are the number of series turns per phase of the stator and the stator winding coefficient, p is the number of pole pairs, A 1 is the straight-line length of the stator winding end extending out, and M 1 is the axial projection length of the stator end winding.

[0035] The rotor of the large-capacity AC excited motor is a wound type. Therefore, the connection method and end winding shape of the motor rotor winding are similar to those of the stator winding. Similarly, the following calculation formula can be used:

[0036]

[0037] Among them, L re is the leakage inductance of the rotor end, N 2 and K w2 are the number of turns in series per phase of the rotor and the rotor winding coefficient, p is the number of pole pairs, A 2 is the straight-line length of the end of the rotor winding extending out, M 2 is the axial projection length of the end winding of the rotor.

[0038] S3. Establish a first simulation model of the motor in the finite element software, run the first simulation model under the rated condition by using the static magnetic field simulation technology of the finite element software, and save the stator permeability and rotor permeability in the first simulation model, as well as the radial magnetic density entering the tooth parts of the stator and rotor.

[0039] Specifically, establish a first simulation model of a large-capacity AC excited motor in the finite element software, obtain the simulation operation results of the large-capacity AC excited motor under the rated condition by using the static magnetic field simulation technology in the finite element software (i.e., the simulation operation results of the first simulation model), and save the stator and rotor permeability information in the first simulation model in combination with the frozen permeability function.

[0040] That is, establish a static field finite element model of a large-capacity AC excited motor (i.e., the first simulation model), set the stator and rotor current excitations to the rated currents of the stator and rotor, run a static field finite element simulation once, and save the permeability information of the entire motor area by using the frozen permeability function built in the finite element software. This permeability information is the permeability information of the motor under the rated condition; and save the radial magnetic density entering the stator tooth part and rotor tooth part.

[0041] S4. Calculate the excitation inductance, stator and rotor harmonic leakage inductances according to the radial magnetic density of the tooth parts of the stator and rotor.

[0042] Specifically, calculate the stator harmonic leakage inductance, rotor harmonic leakage inductance and excitation inductance by using the radial magnetic density entering the stator tooth part and rotor tooth part under the rated condition in step (3).

[0043] The radial magnetic density entering the stator tooth part from the air gap includes the fundamental magnetic density, harmonic magnetic density and a very small part of the tooth tip leakage magnetic density, and this part of the tooth tip leakage magnetic density can be ignored. Perform FFT analysis on the stator radial magnetic density, and then separate the corresponding harmonic magnetic density B h and the fundamental magnetic density B δ , calculate the total harmonic magnetic flux (h = 6k ± 1) and fundamental magnetic flux (h = 1) of the stator according to the following formula, and then calculate the harmonic leakage inductance and excitation inductance of the stator:

[0044]

[0045] Among them, h is the stator harmonic order, l ef , τ, N 1 and K h are respectively the axial length of the motor, the pole pitch, the number of series turns per phase of the stator, and the stator h-th harmonic winding coefficient. B h and Ψ h are the amplitude and magnetic flux of the h-th harmonic magnetic density. I s is the amplitude of the stator current. When h = 1, B h = B δ , and the calculated inductance L h is the excitation inductance, that is, L m ; when h is not 1, the calculated L h is the harmonic leakage inductance of the stator, that is, L shl , h = 6k ± 1, k is 1, 2, 3... Z 1 / (2p), Z 1 is the number of stator slots, p is the number of pole pairs of the motor, and different values of k are used to calculate the harmonic magnetic densities of different h orders.

[0046] Similarly, the calculation method of the rotor harmonic leakage inductance is as follows: perform FFT analysis on the radial magnetic density of the rotor teeth, and then obtain the rotor harmonic magnetic density B rh , and then calculate the harmonic leakage inductance of the rotor:

[0047]

[0048] Among them, h` is the rotor harmonic order, l ef , τ, N 2 and K rh are respectively the axial length of the motor, the pole pitch, the number of series turns per phase of the rotor, and the rotor h`-th harmonic winding coefficient. B rh and Ψ rhl are the amplitude and magnetic flux of the h`-th harmonic magnetic density. I r is the amplitude of the rotor current. h` = 6k` ± 1, k` is 1, 2, 3... Z 2 / (2p), Z 2 is the number of rotor slots, p is the number of pole pairs of the motor, and different values of k` are used to calculate the harmonic magnetic densities of different rotor h` orders.

[0049] S5. Establish the second simulation model of the motor in the finite element software, set its stator magnetic permeability to the stator magnetic permeability in S3, and set its stator ABC three-phase currents to I A , I B , I C, set its rotor permeability to infinitesimal, set the rotor current to 0, run the second simulation model using the static magnetic field simulation technology of the finite element software, and save the magnetic energy storage in the stator slots and the magnetic energy storage W in the air gap ssl and W sgl , according to the formula calculate the stator slot leakage inductance and the stator tooth tip leakage inductance L ssl and L sgl ;

[0050] Establish the third simulation model of the motor in the finite element software, set its rotor permeability to the rotor permeability in S3, and set the rotor UVW three-phase currents to I U 、I V 、I W , set its stator permeability to infinitesimal, set the stator current to 0, run the third simulation model using the static magnetic field simulation technology of the finite element software, and save the magnetic energy storage in the rotor slots and the magnetic energy storage W in the air gap rsl and W rgl , according to the formula calculate the rotor slot leakage inductance and the rotor tooth tip leakage inductance L rsl and L rgl .

[0051] Specifically, establish a static field motor model with the same structure as in S3 in the finite element software, called the second simulation model, and set the mesh division of this model to be consistent with the static field model (i.e., the first simulation model) in S3. Arbitrarily set its stator three-phase currents (which need to satisfy the three-phase symmetry relationship), and set the rotor current to 0 and the rotor region permeability to infinitesimal, such as 10 -7 , so that the magnetic field generated by the stator cannot enter the rotor region, and combine the information of the frozen permeability method in S3 to calculate the stator slot leakage inductance and the stator tooth tip leakage inductance using the energy method. At this time, the stator slot leakage magnetic force lines and the stator tooth tip magnetic force lines are distributed as Figure 3 shown:

[0052] The stator three-phase current excitation satisfies the three-phase symmetry relationship. In the static field, only the current at a certain moment needs to be given for the stator three-phase current excitation. For the convenience of calculation, the stator phase A current I A can be set to the maximum value. At this time, the relationship between the phase B current, the phase C current and the phase A current is According to the energy method, the relationship between the amplitudes of the stator A, B, and C phase currents and the stator slot leakage magnetic energy storage and the stator slot leakage inductance is as follows:

[0053]

[0054] Among them, L sslot 、W sslot and I AThey are the stator slot leakage inductance, the stator slot leakage magnetic energy storage, and the amplitude of the stator current in phase A, respectively.

[0055] Most of the tooth-top leakage magnetic flux lines start from the stator teeth on one side, pass through the air gap, and return to the stator teeth on the other side. Most of the tooth-top leakage magnetic energy storage is contained in the air gap. Therefore, the calculation method for the stator tooth-top leakage inductance can be the same as that for calculating the stator slot leakage inductance. At this time, the area where the energy needs to be calculated is the air gap. Similarly, according to the energy method, the relationships between the amplitudes of the stator A, B, and C phase currents, the stator tooth-top leakage magnetic energy storage, and the stator tooth-top leakage inductance are as follows:

[0056]

[0057] Among them, L sgl and W sgl are the stator tooth-top leakage inductance and the stator tooth-top leakage magnetic energy storage, respectively.

[0058] For example: Establish a static-field motor model in the finite element software with the same structure as in S3, that is, the second simulation model, and set the mesh division of this model to be the same as that of the static-field model in S3. Set the amplitudes of the stator A, B, and C phase currents to 1 A, -0.5 A, and -0.5 A respectively, and set the amplitudes of the rotor U, V, and W phase currents to 0 A. Set the stator permeability to be the same as the stator permeability saved in S3, and set the permeability of the rotor region to 10 -7 , run a static-field simulation, calculate the energy in the stator slots and the energy in the air gap through the simulation software respectively, and calculate the stator slot leakage inductance and the stator tooth-top leakage inductance according to the following formula:

[0059]

[0060] Among them, W ssl and W sgl represent the magnetic energy storage in the stator slots and the magnetic energy storage in the air gap respectively, and L ssl and L sgl represent the stator slot leakage inductance and the stator tooth-top leakage inductance respectively.

[0061] The calculation formulas for the rotor slot leakage inductance and the rotor tooth-top leakage inductance are:

[0062] The calculation methods for the rotor slot leakage inductance and the rotor tooth-top leakage inductance are similar to those of the stator. In terms of setting the excitation currents of the stator and rotor, it is similar to calculating the stator slot leakage inductance and the stator tooth-top leakage inductance. The rotor slot leakage inductance and the rotor tooth-top leakage inductance can be calculated using the following formula:

[0063]

[0064] Among them, W rsl and W rgl represent the magnetic energy storage in the stator slots and the magnetic energy storage in the air gap respectively, and L rsl and Lrgl respectively represent the stator slot leakage inductance and the stator tooth top leakage inductance, I U represents the amplitude of the rotor U-phase current.

[0065] In the finite element software, establish a static field motor model identical to that in S3, called the third simulation model, and set the mesh division of this model to be consistent with the static field model in S3. Arbitrarily set the three-phase rotor currents (which need to satisfy the three-phase symmetry relationship), and set the stator current to 0. Set the magnetic permeability of the stator region to 10 -7 , and combine the information of the frozen magnetic permeability method in S3 and use the energy method to calculate the rotor slot leakage inductance and the rotor tooth top leakage inductance:

[0066] For example, establish a static field motor model identical to that in step S3, and set the mesh division of this model to be consistent with the static field model in step S3. Set the amplitudes of the rotor U, V, and W phase currents to 1A, -0.5A, and -0.5A respectively, set the amplitudes of the stator A, B, and C phase currents to 0A, set the rotor magnetic permeability to be consistent with the magnetic permeability saved in step S3, and set the magnetic permeability of the stator region to 10 -7 , run a static field simulation, calculate the energy in the rotor slot and the energy in the air gap respectively, and calculate the rotor slot leakage inductance and the rotor tooth top leakage inductance according to the following formula,

[0067]

[0068] where, W rsl and W rgl respectively represent the magnetic energy storage in the rotor slot and the magnetic energy storage in the air gap, L rsl and L rgl respectively represent the rotor slot leakage inductance and the rotor tooth top leakage inductance.

[0069] An embodiment of the present invention provides an electronic device, including: a computer-readable storage medium and a processor;

[0070] The computer-readable storage medium is used to store executable instructions;

[0071] The processor is used to read the executable instructions stored in the computer-readable storage medium and execute the method described in any of the above embodiments.

[0072] An embodiment of the present invention provides a computer-readable storage medium, the computer-readable storage medium stores computer instructions, and the computer instructions are used to cause the processor to execute the method described in any of the above embodiments.

[0073] An embodiment of the present invention provides a computer program product, including a computer program or instructions, and when the computer program or instructions are executed by a processor, the method described in any of the above embodiments is implemented.

[0074] Those skilled in the art can easily understand that the above are only preferred embodiments of the present invention and are not intended to limit the present invention. Any modifications, equivalent replacements, and improvements made within the spirit and principles of the present invention shall be included within the protection scope of the present invention.

Claims

1. A method for quickly calculating equivalent circuit parameters of a large-capacity AC excitation motor, characterized in that: include: S1, dividing the stator leakage inductance and rotor leakage inductance of the motor into slot leakage inductance, harmonic leakage inductance, tooth top leakage inductance and end leakage inductance; wherein the motor equivalent circuit parameters include excitation inductance, stator leakage inductance and rotor leakage inductance; S2, selecting a corresponding end leakage inductance calculation formula according to the end winding shape of the motor to calculate the end leakage inductance of the stator and the rotor; S3, establishing a first simulation model of the motor in finite element software, running the first simulation model under rated conditions using static magnetic field simulation technology of the finite element software, and saving the stator magnetic permeability and rotor magnetic permeability in the first simulation model, as well as the radial magnetic flux density entering the teeth of the stator and the rotor; S4, calculating the excitation inductance, the harmonic leakage inductance of the stator and the rotor according to the radial magnetic flux density of the teeth of the stator and the rotor; S5, establishing a second simulation model of the motor in the finite element software, setting its stator magnetic permeability to the stator magnetic permeability in S3, and setting its stator three-phase current I A ,I B ,I C , set its rotor magnetic permeability to infinitesimal, set the rotor current to 0, run the second simulation model using the static magnetic field simulation technology of the finite element software, and save the magnetic energy storage in the stator slot and the magnetic energy storage in the air gap W ssl and W sgl , according to the formula Calculate the stator slot leakage inductance and stator tooth tip leakage inductance L ssl and L sgl ; The third simulation model of the motor is established in the finite element software, and its rotor magnetic permeability is set to the rotor magnetic permeability in S3, and its rotor three-phase current I is set to U ,I V ,I W , set its stator permeability to infinitesimal, set the stator current to 0, use the static magnetic field simulation technology of the finite element software to run the third simulation model, and save the magnetic energy storage in the rotor slot and the magnetic energy storage in the air gap W rsl and W rgl , according to the formula Calculate the rotor slot leakage inductance and rotor tooth tip leakage inductance L rsl and L rgl .

2. The method according to claim 1, characterized in that In step S4, the excitation inductance and the harmonic leakage inductance of the stator are calculated as follows: Perform FFT processing on the radial magnetic flux entering the stator teeth to obtain the corresponding harmonic magnetic flux B h With fundamental magnetic flux density B δ , according to the formula Calculating the excitation inductance and the harmonic leakage inductance of the stator; in, h is the stator harmonic order, l ef , τ, N1 and K h They are the motor axial length, pole pitch, number of series turns per phase of the stator and the stator h-order harmonic winding coefficient, B h and h are the amplitude and flux linkage of the hth stator harmonic flux density, I s is the stator current amplitude; when h = 1, B h =B δ , L h is the magnetizing inductance, i.e. L in the equivalent circuit m ; When h≠1, B h ≠B δ , L h is the harmonic leakage inductance of the stator, i.e. L in the equivalent circuit shl , h=6k±1, k is 1, 2, 3…Z1 / (2p), Z1 is the number of stator slots, and p is the number of motor pole pairs.

3. The method according to claim 1 or 2, characterized in that In step S4, the harmonic leakage inductance of the rotor is calculated as follows: Perform FFT processing on the radial magnetic flux entering the rotor teeth to obtain the corresponding harmonic magnetic flux B rh , according to the formula calculating the harmonic leakage inductance of the rotor; in, h' is the rotor harmonic order, l ef , τ, N2 and K rh are the motor axial length, pole pitch, number of series turns per phase of the rotor and the rotor h' harmonic winding coefficient, B rh , rh and I r They are the amplitude of h` subharmonic magnetic flux, magnetic flux linkage and rotor current amplitude respectively; h`=6k`±1, k` is 1, 2, 3…Z2 / (2p), Z2 is the number of stator slots, and p is the number of motor pole pairs.

4. The method according to claim 1, characterized in that In step S4, the rotor magnetic permeability in the second simulation model is set to 10 -7 ; The stator magnetic permeability in the third simulation model is set to 10 -7 .

5. An electronic device, characterized in that: include: A computer readable storage medium and a processor; The computer-readable storage medium is used to store executable instructions; The processor is used to read the executable instructions stored in the computer-readable storage medium and execute the method according to any one of claims 1 to 4.

6. A computer-readable storage medium, characterized in that: The computer-readable storage medium stores computer instructions, and the computer instructions are used to enable a processor to execute the method according to any one of claims 1 to 4.

7. A computer program product comprising a computer program or instructions, characterized in that When the computer program or instruction is executed by a processor, the method according to any one of claims 1 to 4 is implemented.

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