Power supply control method, power supply control circuit and electronic equipment

Abstract

The invention discloses a power supply control method, a power supply control circuit and electronic equipment. The power supply control method comprises the following steps: acquiring a conduction current instantaneous value in a voltage conversion circuit; carrying out integration processing on the conduction current instantaneous value to obtain a charge integration quantity; converting the pulse reference signal into a target charge quantity; subtracting the charge integral quantity from the target charge quantity to obtain a charge error value; respectively adjusting a preset proportionality coefficient and a preset integral coefficient in response to the level amplitude change of the pulse reference signal to obtain a proportionality adjustment coefficient and an integral adjustment coefficient; and performing proportional-integral adjustment on the charge error value by using the proportional adjustment coefficient and the integral adjustment coefficient to obtain a driving control signal, and sending the driving control signal to a voltage conversion circuit so as to adjust the output current of the voltage conversion circuit. Through the mode, the power supply control method can effectively reduce the rising time and the falling time of the output current, and realizes quick response in a full-load range.

Description

Technical Field

[0001] The present application relates to the technical field of circuit control, and particularly to a power control method, a power control circuit, and an electronic device. Background Art

[0002] Nowadays, with the increasing abundance of electronic devices, the performance requirements for the driving power supplies of electronic devices are becoming increasingly stringent. Especially in the power supply for high-power electronic devices, constant current or constant pulse current driving is required, and high requirements are imposed on the current rise time, fall time, and current ripple.

[0003] However, in the related art, linear power supplies or switching power supplies are usually adopted. However, the linear power supply has large power losses, poor device reliability, and limited output power. Moreover, the current rise time and fall time of the switching power supply are difficult to meet the requirements of fast response. Summary of the Invention

[0004] The main technical problem to be solved by the present application is to provide a power control method, a power control circuit, and an electronic device, which can solve the problems that in the related art, the linear power supply has large power losses, poor device reliability, limited output power, and the current rise time and fall time of the switching power supply are difficult to meet the requirements of fast response.

[0005] To solve the above technical problem, a technical solution adopted by the present application is: providing a power control method applied to the power control of a voltage conversion circuit. Wherein, the power control method includes: obtaining the instantaneous value of the conduction current in the voltage conversion circuit; performing integral processing on the instantaneous value of the conduction current to obtain a charge integral amount; obtaining a pulse reference signal, a preset proportional coefficient, and a preset integral coefficient; converting the pulse reference signal into a target charge amount; subtracting the charge integral amount from the target charge amount to obtain a charge error value; adjusting the preset proportional coefficient and the preset integral coefficient respectively in response to the change in the level amplitude of the pulse reference signal to obtain a proportional adjustment coefficient and an integral adjustment coefficient; performing proportional-integral adjustment on the charge error value by using the proportional adjustment coefficient and the integral adjustment coefficient to obtain a drive control signal; and sending the drive control signal to the voltage conversion circuit to trigger the voltage conversion circuit to change the switching state, thereby adjusting the output current of the voltage conversion circuit.

[0006] Wherein, the step of adjusting the preset proportional coefficient and the preset integral coefficient respectively in response to the change in the level amplitude of the pulse reference signal to obtain a proportional adjustment coefficient and an integral adjustment coefficient includes: obtaining the rising edge of the pulse reference signal; multiplying the preset proportional coefficient by a first proportional rising factor in response to the rising edge to obtain a proportional adjustment coefficient; and multiplying the preset integral coefficient by a first integral rising factor to obtain an integral adjustment coefficient.

[0007] Among them, the steps of adjusting the preset proportional coefficient and the preset integral coefficient in response to the change in the level amplitude of the pulse reference signal to obtain the proportional adjustment coefficient and the integral adjustment coefficient include: obtaining the falling edge of the pulse reference signal; multiplying the preset proportional coefficient by the first proportional decrease factor in response to the falling edge to obtain the proportional adjustment coefficient; multiplying the preset integral coefficient by the first integral decrease factor to obtain the integral adjustment coefficient.

[0008] Among them, the steps of adjusting the preset proportional coefficient and the preset integral coefficient respectively in response to the change in the level amplitude of the pulse reference signal to obtain the proportional adjustment coefficient and the integral adjustment coefficient include: obtaining the level change error value of the pulse reference signal; detecting whether the level change error value is within the preset error threshold range; if the level change error value is greater than the preset error threshold range; multiplying the preset proportional coefficient by the second proportional increase factor to obtain the proportional adjustment coefficient; multiplying the preset integral coefficient by the second integral increase factor to obtain the integral adjustment coefficient.

[0009] Among them, the step of multiplying the preset proportional coefficient by the second proportional increase factor to obtain the proportional adjustment coefficient includes: obtaining the proportional increase correction factor by using the level change error value; wherein, the proportional increase correction factor is positively correlated with the level change error value; after multiplying the preset proportional coefficient by the second proportional increase factor, multiplying it by the proportional increase correction factor to obtain the proportional adjustment coefficient.

[0010] Among them, the step of obtaining the increase correction factor by using the level change error value includes: performing arithmetic processing on the level change error value by using a preset correction function or a preset mapping relation table to obtain the proportional increase correction factor and the integral increase correction factor.

[0011] Among them, the step of multiplying the preset integral coefficient by the second integral increase factor to obtain the integral adjustment coefficient includes: obtaining the integral increase correction factor by using the level change error value; wherein, the integral increase correction factor is positively correlated with the level change error value; after multiplying the preset integral coefficient by the second integral increase factor, multiplying it by the integral increase correction factor to obtain the integral adjustment coefficient.

[0012] Among them, the power control method further includes: if the level change error value is less than the preset error threshold range; multiplying the preset proportional coefficient by the second proportional decrease factor to obtain the proportional adjustment coefficient; multiplying the preset integral coefficient by the second integral decrease factor to obtain the integral adjustment coefficient.

[0013] Among them, the step of multiplying the preset proportional coefficient by the second proportional decrease factor to obtain the proportional adjustment coefficient includes: obtaining the proportional decrease correction factor by using the level change error value; wherein, the proportional decrease correction factor is positively correlated with the level change error value; after multiplying the preset proportional coefficient by the second proportional decrease factor, multiplying it by the proportional decrease correction factor to obtain the proportional adjustment coefficient.

[0014] Among them, the step of multiplying a preset integral coefficient by a second integral reduction factor to obtain an integral adjustment coefficient includes: obtaining an integral reduction correction factor by using a level change error value; wherein, the integral reduction correction factor is positively correlated with the level change error value; after multiplying the preset integral coefficient by the second integral reduction factor, multiplying the result by the integral reduction correction factor to obtain the integral adjustment coefficient.

[0015] Among them, the step of performing proportional-integral adjustment on the charge error value by using the proportional adjustment coefficient and the integral adjustment coefficient to obtain a drive control signal includes: obtaining an output current; subtracting the output current from the pulse reference signal to obtain a current error value; obtaining a proportional control factor coefficient and an integral control factor coefficient by using the current error value; wherein, both the proportional control factor coefficient and the integral control factor coefficient are positively correlated with the current error value; multiplying the proportional adjustment coefficient by the proportional control factor coefficient to obtain a proportional control coefficient; multiplying the integral adjustment coefficient by the integral control factor coefficient to obtain an integral control coefficient; performing proportional-integral adjustment on the charge error value by using the proportional control coefficient and the integral control coefficient to obtain the drive control signal.

[0016] Among them, the proportional control factor coefficient includes an increasing proportional control factor coefficient and a decreasing proportional control factor coefficient, and the proportional control coefficient includes an increasing proportional control coefficient and a decreasing proportional control coefficient. The step of multiplying the proportional adjustment coefficient by the proportional control factor coefficient to obtain the proportional control coefficient includes: in response to an increase in the current error value, multiplying the proportional adjustment coefficient by the increasing proportional control factor coefficient to obtain the increasing proportional control coefficient; in response to a decrease in the current error value, multiplying the proportional adjustment coefficient by the decreasing proportional control factor coefficient to obtain the decreasing proportional control coefficient.

[0017] Among them, the integral control factor coefficient includes an increasing integral control factor coefficient and a decreasing integral control factor coefficient, and the integral control coefficient includes an increasing integral control coefficient and a decreasing integral control coefficient. The step of multiplying the integral adjustment coefficient by the integral control factor coefficient to obtain the integral control coefficient includes: in response to an increase in the current error value, multiplying the integral adjustment coefficient by the increasing integral control factor coefficient to obtain the increasing integral control coefficient; in response to a decrease in the current error value, multiplying the integral adjustment coefficient by the decreasing integral control factor coefficient to obtain the decreasing integral control coefficient.

[0018] To solve the above technical problems, another technical solution adopted by this application is: providing a power supply control circuit, wherein, the power supply control circuit is coupled to a voltage conversion circuit; wherein, the power supply control circuit controls the power supply of the voltage conversion circuit by using the power supply control method described in any one of the above.

[0019] To solve the above technical problems, yet another technical solution adopted by this application is: providing an electronic device, wherein, the electronic device includes a housing and a power supply control circuit connected to the housing; wherein, the power supply control circuit is the power supply control circuit described above.

[0020] The beneficial effects of the present application are as follows: Different from the prior art, the power control method provided by the present application obtains the instantaneous value of the conduction current in the voltage conversion circuit, integrates the instantaneous value of the conduction current to obtain the charge integration amount, and obtains the pulse reference signal, the preset proportional coefficient, and the preset integration coefficient, so as to convert the pulse reference signal into the target charge amount, subtract the charge integration amount from the target charge amount to obtain the charge error value, and when the level amplitude of the pulse reference signal changes, adjust the preset proportional coefficient and the preset integration coefficient respectively to obtain the proportional adjustment coefficient and the integration adjustment coefficient, so as to perform proportional-integral adjustment on the charge error value by using the proportional adjustment coefficient and the integration adjustment coefficient to obtain the drive control signal. Therefore, it can respond to the change in the level amplitude of the pulse reference signal, that is, when the load state changes, by adjusting the preset proportional coefficient and the preset integration coefficient, the obtained drive control signal can more quickly adjust the output current of the voltage conversion circuit to the current amplitude range required by the changed load state, so as to effectively reduce the rise time and fall time of the output current, thereby achieving fast response in the full load range; and there is no need to make the corresponding power device work in the linear region, the power loss is low, the reliability is good, and the output power does not need to be limited. Description of the Drawings

[0021] In order to more clearly illustrate the technical solutions in the embodiments of the present application, the following will briefly introduce the drawings required for the description of the embodiments. Obviously, the following drawings are only some embodiments of the present application. For those of ordinary skill in the art, without creative efforts, other drawings can be obtained according to these drawings, where: Figure 1 is a schematic flowchart of the first embodiment of the power control method of the present application; Figure 2 is a schematic structural diagram of the first embodiment of the power control circuit of the present application; Figure 3 is Figure 1 a schematic flowchart of the first embodiment of S16 in Figure 4 is Figure 1 a schematic flowchart of the second embodiment of S16 in Figure 5 is Figure 1 a schematic flowchart of the third embodiment of S16 in Figure 6 is a schematic structural diagram of the second embodiment of the power control circuit of the present application; Figure 7 is a schematic structural diagram of the third embodiment of the power control circuit of the present application; Figure 8 isFigure 5 Flow schematic diagram of an embodiment of S1633; Figure 9 is Figure 5 Flow schematic diagram of an embodiment of S1634; Figure 10 is Figure 5 Flow schematic diagram of an embodiment of S1636; Figure 11 is Figure 5 Flow schematic diagram of an embodiment of S1637; Figure 12 is Figure 1 Flow schematic diagram of an embodiment of S17; Figure 13 is Figure 12 Flow schematic diagram of an embodiment of S174; Figure 14 is Figure 12 Flow schematic diagram of an embodiment of S175; Figure 15 Structural schematic diagram of an embodiment of the electronic device of the present application. Specific implementation manners

[0022] Next, the technical solutions in the embodiments of the present application will be clearly and completely described in conjunction with the accompanying drawings in the embodiments of the present application. Obviously, the described embodiments are only a part of the embodiments of the present application, rather than all the embodiments. Based on the embodiments in the present application, all other embodiments obtained by those of ordinary skill in the art without creative efforts fall within the protection scope of the present application.

[0023] The terms "first", "second", and "third" in the present application are only for descriptive purposes, and cannot be understood as indicating or implying relative importance or implicitly specifying the quantity of the indicated technical features. Thus, the features defined with "first", "second", and "third" may explicitly or implicitly include at least one of such features. In the description of the present application, the meaning of "a plurality" is at least two, such as two, three, etc., unless otherwise specifically defined. All directional indications (such as up, down, left, right, front, back...) in the embodiments of the present application are only used to explain the relative position relationship and movement conditions between components in a specific posture (as shown in the drawings). If the specific posture changes, the directional indications will also change accordingly. In addition, the terms "include" and "have" and any variations thereof are intended to cover non-exclusive inclusion. For example, a process, method, system, product, or device that includes a series of steps or units is not limited to the listed steps or units, but optionally further includes steps or units not listed, or optionally further includes other steps or units inherent to these processes, methods, products, or devices.

[0024] As used herein, the term "embodiment" means that a particular feature, structure, or characteristic described in connection with an embodiment can be included in at least one embodiment of the present application. The phrase may appear in various places in the specification and does not necessarily refer to the same embodiment, nor is it an independent or alternative embodiment that is mutually exclusive with other embodiments. Those skilled in the art will explicitly and implicitly understand that the embodiments described herein can be combined with other embodiments.

[0025] The present application will be described in detail below with reference to the accompanying drawings and embodiments.

[0026] Please refer to Figure 1 and Figure 2 , where Figure 1 is a schematic flowchart of the first embodiment of the power control method of the present application, Figure 2 is a schematic structural diagram of the first embodiment of the power control circuit of the present application. Specifically, the following steps may be included: S11: Obtain the instantaneous value of the conduction current in the voltage conversion circuit.

[0027] It can be understood that the power control method in this embodiment is specifically applied to the power control of the first voltage conversion circuit 30 as shown in Figure 2 . Among them, the first power control circuit 20 is coupled to the first voltage conversion circuit 30, and the power control method described in any item herein is used to implement power control on the first voltage conversion circuit 30.

[0028] It should be noted that the first voltage conversion circuit 30 may specifically be a single-phase BUCK circuit (step-down conversion circuit), a multi-phase BUCK circuit, or a BOOST circuit (step-up conversion circuit), or any other reasonable form of circuit topology, and this embodiment does not limit this.

[0029] In some embodiments, the first power control circuit 20 may specifically include a control chip, a DSP (Digital Signal Processing) chip, an MCU (Micro Controller Unit) circuit, a CPU (Central Processing Unit), a single-chip microcomputer, a field programmable gate array, a programmable logic device, discrete gates, or transistor logic devices, discrete hardware, or any other reasonable circuit unit with signal processing functions, and the present application does not limit this.

[0030] In addition, "coupled" in this article refers to including any direct and indirect connection means. Therefore, if it is described in the article that the first circuit is coupled to the second circuit, it means that the first circuit can be directly connected to the second circuit through electrical connection, wireless transmission, optical transmission or other signal connection means, or indirectly electrically connected or signal connected to the second circuit through other circuits or connection means.

[0031] Specifically, the first power control circuit 20 monitors in real time the instantaneous current amplitude when the switching element inside the first voltage conversion circuit 30 is triggered to conduct, that is, the instantaneous conduction current value Iphase.

[0032] Among them, the instantaneous conduction current value Iphase can be specifically obtained by any reasonable sampling method such as a high-precision current sensor, resistor, Hall sensor or circuit model estimation. This application does not make any limitations on this.

[0033] S12: Perform an integration process on the instantaneous conduction current value to obtain a charge integration amount.

[0034] Integrate the instantaneous conduction current value Iphase within one cycle to obtain the charge integration amount Qphase within this cycle, that is, Qphase = ∫Iphase dt.

[0035] S13: Obtain a pulse reference signal, a preset proportional coefficient, and a preset integral coefficient.

[0036] For the specific working conditions and power supply requirements of the load circuit, a set of appropriate PI (Proportional Integral) reference values, that is, a preset proportional coefficient kp0 and a preset integral coefficient ki0, are obtained through experimental calibration or simulation optimization, and a reference pulse current is set, or the reference pulse current, preset proportional coefficient kp0, and preset integral coefficient ki0 input by the host computer are received, so that the first voltage conversion circuit 30 has excellent current rise time and current fall time under this working condition.

[0037] Among them, the reference pulse current can specifically be a periodic pulse waveform or other forms of reference signals.

[0038] It is worth noting that in order to satisfy that when the output current Io jumps arbitrarily, the first voltage conversion circuit 30 can achieve a fast response to obtain a sufficiently short current rise time and fall time, the PI parameters should be adjusted according to the current load state, and first obtain the PI reference values with the change of the load state from no load to full load as a reference, and adjust the PI reference values in response to the change of other load states.

[0039] In addition, the host computer usually refers to a computer system with powerful computing and data processing capabilities. It is responsible for the monitoring, instruction issuing, data acquisition, processing and analysis, and user interaction of the entire control system. As the "brain" of the system, the host computer can process complex algorithms, perform long-term data storage, and provide a graphical interface for users to operate.

[0040] The slave computer refers to a device or controller directly connected to hardware such as sensors and actuators in the control system. It is responsible for executing specific control instructions issued by the host computer, such as the output of switch signals, the adjustment of analog quantities, and the acquisition of data. The slave computer usually performs simple logical judgments and real-time control tasks.

[0041] S14: Convert the pulse reference signal into a target charge amount.

[0042] Integrate the pulse reference signal Iref within one period to obtain the corresponding target charge amount Qref.

[0043] S15: Subtract the charge integration amount from the target charge amount to obtain the charge error value.

[0044] Subtract the charge integration amount Qphase from the target charge amount Qref to calculate the charge error value Qer between the actual charge and the target charge, that is, Qer = Qref - Qphase.

[0045] S16: Adjust the preset proportional coefficient and the preset integral coefficient respectively in response to the change in the level amplitude of the pulse reference signal to obtain the proportional adjustment coefficient and the integral adjustment coefficient.

[0046] When it is detected that the amplitude of the pulse reference signal Iref changes, for example, jumps from a low level to a high level, or from a high level to a low level, adjust the preset proportional coefficient kp0 according to the change amplitude to obtain the proportional adjustment coefficient kpt, and adjust the preset integral coefficient ki0 to obtain the integral adjustment coefficient kit.

[0047] Among them, the adjustment function or mapping relationship corresponding to the adjustment of the preset proportional coefficient kp0 and the preset integral coefficient ki0 can specifically be a linear or non-linear mapping; and when the change amplitude of the pulse reference signal Iref is the same but the change directions are different, that is, the adjustment functions or mapping relationships corresponding to jumping from a low level to a high level and jumping from a high level to a low level are different.

[0048] It should be noted that the load states of the first voltage conversion circuit 30 generally include no-load, light load, full load, and overload. Among them, no-load refers to the operating state where the device or system is not connected to any load; the load is significantly lower than the rated capacity, and the specific ratio varies in different fields. Generally, it means that the load rate is below 30% of the rated power (or defined as below 50% in some scenarios); full load means that the load is close to or equal to the rated capacity, such as when the output power of the generator is consistent with the nameplate nominal value; overload means that the load exceeds the rated capacity.

[0049] In addition, the load rate is a core parameter that measures the relationship between the actual operating load of a device or system and its rated capacity, and its definition and calculation method vary depending on the application field.

[0050] General definition: Load rate = actual load / rated load * 100%, which is applicable to scenarios such as transformers, motors, and power systems. For example: The load rate of a transformer is the ratio of the output apparent power to the rated capacity.

[0051] Among them, the level amplitude of the pulse reference signal Iref is determined by the current load state, and for different load states, its level amplitude is different; or it can be understood that at different load rates of the first voltage conversion circuit 30, the pulse reference signal Iref has different level amplitudes, and the level amplitude of the pulse reference signal Iref and the load rate satisfy a specific functional relationship or mapping relationship.

[0052] The change in the level amplitude of the pulse reference signal Iref corresponds to a change in the load state of the first voltage conversion circuit 30. For example, jumping from no-load to light load, or from light load to overload, or from full load to no-load, etc., any reasonable state change; it can also correspond to any reasonable change range of the load rate, such as jumping from 0 to 30%, or from 20% to 80%, or from 100% to 50%, etc. This application does not make any limitations in this regard.

[0053] S17: Using the proportional adjustment coefficient and the integral adjustment coefficient to perform proportional-integral adjustment on the charge error value to obtain a drive control signal.

[0054] Using the updated proportional adjustment coefficient kpt and the integral adjustment coefficient kit to perform proportional-integral adjustment on the charge error value Qer to output a reference signal for modulating the duty cycle, that is, the drive control signal PWM.

[0055] In some embodiments, the drive control signal PWM can specifically be one or more of any reasonable control signals such as a PWM (Pulse Width Modulation) signal or a PFM (Pulse Frequency Modulation) signal, etc. This application does not make any limitations in this regard.

[0056] S18: Send the drive control signal to the voltage conversion circuit to trigger the voltage conversion circuit to change its switching state, thereby adjusting the output current of the voltage conversion circuit.

[0057] Send the drive control signal PWM to the first voltage conversion circuit 30 to control the on or off of the switching element in the first voltage conversion circuit 30, thereby adjusting the output current Io to approximate the reference waveform.

[0058] In the above solution, in response to the change in the level amplitude of the pulse reference signal Iref, that is, when the load state changes, by adjusting the preset proportional coefficient kp0 and the preset integral coefficient ki0, the resulting drive control signal PWM can more quickly adjust the output current Io of the first voltage conversion circuit 30 to the current amplitude range required by the changed load state, so as to effectively reduce the rise time and fall time of the output current Io, thereby achieving fast response within the full load range; and there is no need to make the corresponding power device work in the linear region, with low power loss, good reliability, and the output power does not need to be limited.

[0059] Moreover, by adopting the first voltage conversion circuit 30 under charge control, on the basis of reducing the ripple of the output current Io, using the principle of directly implementing closed-loop control on the charge quantity by charge control, the power supply response speed can be effectively improved; combined with a dynamic PI controller, according to different output currents Io and pulse phases, that is, different pulse reference signals Iref, appropriate PI parameters are adjusted, so that the first voltage conversion circuit 30 can quickly respond to any load mutation within the full load range, and on the basis of reducing the output overshoot, the first voltage conversion circuit 30 has a sufficiently short current rise time and fall time.

[0060] Adjust the PI parameters in real time according to the change in the reference signal amplitude to improve the response speed and stability of the system under sudden load. Automatically optimize the control parameters when switching between light load and heavy load, taking into account both efficiency and output accuracy. Closed-loop control based on charge error; adaptive parameter adjustment for reference signal changes; more stable and efficient current regulation performance; supporting various topologies and complex load requirements. This is a highly flexible, responsive, and stable control scheme, suitable for the design and implementation of modern high-performance power management systems.

[0061] Please continue to refer to Figure 3 , Figure 3 which Figure 1 is the flow schematic diagram of the first embodiment of S16. In one embodiment, the power supply control method of the present application further includes some more specific steps in addition to the above S11 - S18. Specifically, the above S16 may further include the following steps: S1611: Obtain the rising edge of the pulse reference signal.

[0062] It can be understood that the pulse reference signal Iref has a transition from a low level to a high level, that is, a rising edge, and a transition from a high level to a low level, that is, a falling edge.

[0063] Specifically, the first power control circuit 20 identifies and detects the rising edge of the pulse reference signal Iref. For example, this can be achieved by any reasonable means such as a hardware circuit (such as an edge trigger), a software algorithm (for example, writing corresponding code in an embedded system), or a controller counter. The present application does not limit this.

[0064] S1612: Multiply a preset proportional coefficient by a first proportional rising factor in response to the rising edge to obtain a proportional adjustment coefficient.

[0065] When the rising edge of the pulse reference signal Iref is detected, multiply the preset proportional coefficient kp0 by the first proportional rising factor bs1 to calculate the proportional adjustment coefficient kpt, that is, kpt = kp0 * bs1.

[0066] S1613: Multiply a preset integral coefficient by a first integral rising factor to obtain an integral adjustment coefficient.

[0067] Multiply the preset integral coefficient ki0 by the first integral rising factor js1 to calculate the integral adjustment coefficient kit, that is, kit = ki0 * js1.

[0068] In some embodiments, the first proportional rising factor bs1 and the first integral rising factor js1 may be the same or different specifically; and the first proportional rising factor bs1 and the first integral rising factor js1 may respectively be different or the same in response to the amplitude change of the pulse reference signal Iref level, that is, the difference between the level amplitude before the step change and the level amplitude after the step change of the pulse reference signal Iref, and can be specifically set by fitting according to simulation prediction or experimental optimization. The present application does not limit this.

[0069] Please continue to refer to Figure 4 , Figure 4 is Figure 1 the flow schematic diagram of the second embodiment of S16 in . In one embodiment, the power control method of the present application further includes some more specific steps in addition to the above S11 - S18. Specifically, the above S16 may further include the following steps: S1621: Obtain the falling edge of the pulse reference signal.

[0070] Specifically, the first power control circuit 20 identifies and detects the falling edge of the pulse reference signal Iref. For example, this can be achieved by any reasonable means such as a hardware circuit (e.g., an edge trigger), a software algorithm (e.g., writing corresponding code in an embedded system), or a controller counter. The present application does not limit this.

[0071] S1622: In response to the falling edge, multiply the preset proportionality coefficient by the first proportionality decrease factor to obtain the proportionality adjustment coefficient.

[0072] Similarly, when the falling edge of the pulse reference signal Iref is detected, multiply the preset proportionality coefficient kp0 by the first proportionality decrease factor bj1 to calculate the proportionality adjustment coefficient kpt, that is, kpt = Iref * bj1.

[0073] S1623: Multiply the preset integral coefficient by the first integral decrease factor to obtain the integral adjustment coefficient.

[0074] Multiply the preset integral coefficient ki0 by the first integral decrease factor jj1 to calculate the integral adjustment coefficient kit, that is, kit = ki0 * jj1.

[0075] In some embodiments, when the currently obtained level change error value Ver is the same, the first proportionality decrease factor bj1 is different from the first proportionality increase factor bs1, and the first integral decrease factor jj1 is different from the first integral increase factor js1.

[0076] In some embodiments, the first proportionality decrease factor bj1 and the first integral decrease factor jj1 may specifically be the same or different; and the first proportionality decrease factor bj1 and the first integral decrease factor jj1 can respectively respond to the amplitude change of the pulse reference signal Iref, that is, the difference between the level amplitude before the step change and the level amplitude after the step change of the pulse reference signal Iref, and can be the same or different, and can specifically be obtained by fitting and setting according to simulation prediction or experimental optimization. The present application does not limit this.

[0077] When the falling edge of the drive control signal PWM is detected, reset and clear the charge integration amount Qphase to wait for the next rising edge to re-integrate the instantaneous value of the conduction current Iphase.

[0078] Please refer to Figure 5 , Figure 5 is Figure 1 the flowchart of the third embodiment of S16 in. In one embodiment, the power control method of the present application further includes some more specific steps in addition to the above S11 - S18. Specifically, the above S16 can further include the following steps: S1631: Obtain the level change error value of the pulse reference signal.

[0079] Please continue to refer to Figure 6 , Figure 6 which is a schematic structural diagram of the second embodiment of the power control circuit of the present application.

[0080] It can be understood that the power control method in this embodiment may specifically be that the second power control circuit 40 adjusts the current for the second voltage conversion circuit 50 as shown in Figure 6 . Among them, the second voltage conversion circuit 50 includes a switch sub-circuit 51 and an adjustment output sub-circuit 52; the switch sub-circuit 51 includes a first upper switch tube Q H 1 and a first lower switch tube Q L 1, and the adjustment output sub-circuit 52 includes a first capacitor C1, a second capacitor C2, a first upper diode D H 1, a first lower diode D L 1, a first inductor L1, and an output capacitor Co, corresponding to a single-phase BUCK circuit.

[0081] Among them, the first end of the first capacitor C1 is coupled to the first end of the first upper switch tube Q H 1 and is used to be coupled to the first end of the DC power supply DC. The second end of the first capacitor C1 is coupled to the first end of the second capacitor C2, the first end of the first upper diode Q H 1, and the second end of the first lower diode Q L 1. The second end of the second capacitor C2 is coupled to the first end of the first lower switch tube Q L 1 and is used to be coupled to the second end of the DC power supply DC and grounded. The second end of the first upper switch tube Q H 1 is coupled to the second end of the first upper diode D H 1 and the first end of the first inductor L1. The second end of the first inductor L1 is coupled to the first end of the output capacitor Co and is used to be coupled to the first end of the equivalent series diode Do in the load circuit 101. The second end of the first lower switch tube Q L 1 is coupled to the first end of the first upper diode D H 1 and the second end of the output capacitor Co and is used to be coupled to the second end of the equivalent series diode Do in the load circuit 101.

[0082] In other embodiments, the load circuit 101 may specifically further include one or more of any reasonable circuit elements such as an equivalent resistor, an equivalent capacitor, and an equivalent series diode. The present application does not make any limitations thereto.

[0083] Among them, the second power control circuit 40 specifically further includes a charge sampling and integrating circuit 41 and a dynamic control circuit 42. The charge sampling and integrating circuit 41 further includes a current sampling circuit 411, a charge integrating circuit 412, and a charge feedback control circuit 413. Among them, the current sampling circuit 411 is coupled to the first end of the first upper switching transistor Q H 1 and / or the first end of the first lower switching transistor Q L 1, and is coupled to the charge integrating circuit 412. The charge integrating circuit 412 is coupled to the charge feedback control circuit 413. The charge feedback control circuit 413 is coupled to the dynamic control circuit 42, the third end of the first upper diode D H 1, and the third end of the first lower diode D L 1.

[0084] In some embodiments, the first upper switching transistor Q H 1 and the first lower switching transistor Q L 1 can specifically be one of a MOSFET (Metal Oxide Semiconductor Field Effect Transistor), a triode, a thin film transistor, a field effect transistor, or any other reasonable switching transistor. The present application does not limit this.

[0085] Please continue to refer to Figure 7 , Figure 7 which is a schematic structural diagram of the third embodiment of the first power control circuit of the present application.

[0086] In some other embodiments, the second voltage conversion circuit 50 can specifically also be a multi-phase BUCK circuit. That is, the switching sub-circuit 51 can specifically also include a first upper switching transistor Q H 1, a second upper switching transistor Q H 2,..., an nth upper switching transistor Q H n (n is an integer greater than 1), a first lower switching transistor Q L 1, a second lower switching transistor Q L 2,..., an nth lower switching transistor Q L n; the regulated output sub-circuit 52 includes a first capacitor C1, a second capacitor C2, a first upper diode D H 1, a second upper diode D H 2,..., an nth upper diode D H n, a first lower diode D L 1, a second lower diode D L 2,..., an nth lower diode D L n, a first inductor L1, a second inductor L2,..., an nth inductor Ln, and an output capacitor Co.

[0087] Among them, the first end of the first capacitor C1 is coupled to the first end of the first upper switch transistor Q H 1, the first end of the second upper switch transistor Q H 2,..., the first end of the nth upper switch transistor Q H n, and is used to be coupled to the first end of the DC power supply DC. The second end of the first capacitor C1 is coupled to the first end of the second capacitor C2, the first end of the first upper diode D H 1, the first end of the second upper diode D H 2,..., the first end of the nth upper diode D H n, and the second end of the first lower diode D L 1, the second end of the second lower diode D L 2,..., the second end of the nth lower diode D L n. The second end of the second capacitor C2 is coupled to the first end of the first lower switch transistor Q L 1, the first end of the second lower switch transistor Q L 2,..., the first end of the nth lower switch transistor Q L n, and is used to be coupled to the second end of the DC power supply DC and grounded. The second end of the first upper switch transistor Q H 1, the second end of the second upper switch transistor Q H 2,..., the second end of the nth upper switch transistor Q H n are respectively coupled to the second end of the first upper diode D H 1, the second end of the second upper diode D H 2,..., the second end of the nth upper diode D H n, and the first end of the first inductor L1, the first end of the second inductor L2,..., the first end of the nth inductor Ln. The second end of the first inductor L1 is coupled to the second end of the second inductor L2,..., the second end of the nth inductor Ln and the first end of the output capacitor Co, and is used to be coupled to the first end of the equivalent series diode Do in the load circuit 101. The second end of the first lower switch transistor Q L 1, the second end of the second lower switch transistor Q L 2,..., the second end of the nth lower switch transistor Q L n are respectively coupled to the first end of the first upper diode D H 1, the first end of the second upper diode D H 2,..., the first end of the nth upper diode D H n and the second end of the output capacitor Co, and are used to be coupled to the second end of the equivalent series diode Do in the load circuit 101.

[0088] Of course, in other embodiments, the second voltage conversion circuit 50 may specifically be a multi-phase interleaved BOOST circuit (boost conversion circuit), a single-phase BOOST circuit, or other forms of circuit topologies, and this embodiment does not limit this.

[0089] For ease of understanding, taking the second voltage conversion circuit 50 as a single-phase BUCK circuit as an example for illustration, the dynamic control circuit 42 sets a pulse reference signal Iref, or receives the pulse reference signal Iref sent by the host computer, to detect the change in the level amplitude of the pulse reference signal Iref in real time, and calculates the level change error value Ver between the level amplitude V1 before the step change and the level amplitude V2 after the step change of the pulse reference signal Iref, that is, Ver = V2 - V1.

[0090] Among them, the host computer can be specifically understood as a system processor that monitors and controls the working state and application scenario of the load circuit to determine the current power supply demand of the load circuit, such as the demand for output power or output current Io of the load circuit, and then sets the pulse reference signal Iref.

[0091] S1632: Detect whether the level change error value is within a preset error threshold range.

[0092] It is worth noting that in some application scenarios, to ensure better power supply quality, different PI parameters will correspond to the increase and decrease of the level amplitude of the pulse reference signal Iref. For example, when the first voltage conversion circuit 30 specifically supplies power to the laser pump source, since the load characteristic of the laser pump source is equivalent to a model in which multiple ideal diodes are connected in series with a resistor, different from a constant voltage output power supply, the output voltage Vo of the first voltage conversion circuit 30 will change under different output currents Io. Therefore, for a laser pump source driven by a pulsed current, in the rising or falling stage of the current pulse signal, the first voltage conversion circuit 30 has different demagnetizing voltages. Specifically, when the input voltage Vin remains unchanged, in the rising stage of the current pulse signal, the output voltage Vo is relatively low, and the demagnetizing voltage Vc is equal to the input voltage Vin minus the output voltage Vo, that is, Vc = Vin - Vo, which is relatively large; in the falling stage of the current pulse signal, the output voltage Vo is relatively high, and the demagnetizing voltage Vc is equal to the input voltage Vin minus the output voltage Vo, which is relatively small.

[0093] Therefore, for the rising or falling stage of the current pulse signal, if the same set of PI parameters is used for adjustment, it will inevitably lead to an excessive current rising slope resulting in current overshoot, or an excessively small current falling slope resulting in an overly long current falling time, and neither result is a desired situation in the field of laser power supplies.

[0094] It can be seen from this that after obtaining the level change error value Ver, it is necessary to further judge and distinguish its positive and negative values to determine the current change trend of the pulse reference signal Iref.

[0095] It is understandable that this preset error threshold range is a level amplitude range reasonably set to distinguish whether the pulse reference signal Iref is increasing positively, decreasing negatively, or remaining unchanged within a relatively stable threshold range.

[0096] Specifically, the dynamic control circuit 42 is used to detect whether the currently obtained level change error value Ver is within the preset error threshold range. When it is detected that the level change error value Ver is greater than the preset error threshold range, it is determined that the pulse reference signal Iref is increasing positively, that is, the current pulse signal step changes to the rising stage; when it is detected that the level change error value Ver is less than the preset error threshold range, it is determined that the pulse reference signal Iref is decreasing negatively, that is, the current pulse signal step changes to the falling stage; when it is detected that the level change error value Ver is within the preset error threshold range, it is determined that the pulse reference signal Iref remains unchanged, that is, the current pulse signal does not undergo a step change.

[0097] In some embodiments, the absolute value of the upper limit value of the preset error threshold range is equal to that of the lower limit value, and it is 5%-10% of the maximum value of the externally input pulse reference signal Iref, that is, 5%-10% of the pulse reference signal Iref obtained when the current load state is the full-load state, and preferably 6% of the maximum value of the pulse reference signal Iref. This application does not make any limitations in this regard.

[0098] Among them, if the level change error value Ver is greater than the preset error threshold range, then execute S1633; if the level change error value Ver is within the preset error threshold range, then execute S1635; if the level change error value Ver is less than the preset error threshold range, then execute S1637.

[0099] S1633: Multiply the preset proportional coefficient by the second proportional rising factor to obtain the proportional adjustment coefficient.

[0100] Specifically, the current sampling circuit 411 is used to monitor in real time the instantaneous current amplitude when the switching element inside the first voltage conversion circuit 30 is triggered to conduct, so as to obtain the instantaneous conduction current value Iphase.

[0101] The charge integration circuit 412 integrates the instantaneous conduction current value Iphase within one period to obtain the charge integration amount Qphase within this period.

[0102] The charge feedback control circuit 413 obtains a set of suitable PI reference values, namely a preset proportional coefficient kp0 and a preset integral coefficient ki0, through experimental calibration or simulation optimization, and sets a pulse reference current Iref, or receives the pulse reference current Iref, the preset proportional coefficient kp0, and the preset integral coefficient ki0 input by the host computer.

[0103] Furthermore, when the charge feedback control circuit 413 determines that the currently obtained level change error value Ver is greater than the preset error threshold range by using the dynamic control circuit 42, it multiplies the preset proportional coefficient kp0 by a second proportional rising factor bs2 to obtain a proportional adjustment coefficient kpt, that is, kpt = kp0 * bs2.

[0104] S1634: Multiply the preset integral coefficient by a second integral rising factor to obtain an integral adjustment coefficient.

[0105] The charge feedback control circuit 413 multiplies the preset proportional coefficient kp0 by a second proportional rising factor bs2 to obtain a proportional adjustment coefficient kpt, that is, kpt = kp0 * bs2.

[0106] In some embodiments, the second proportional rising factor bs2 and the second integral rising factor js2 may be the same or different; and the second proportional rising factor bs2 and the second integral rising factor js2 can respectively respond to the amplitude change of the pulse reference signal Iref, that is, they are different or the same according to the difference between the level amplitude before the step change and the level amplitude after the step change of the pulse reference signal Iref, and can be specifically set by fitting according to simulation prediction or experimental optimization, and the present application does not limit this.

[0107] S1635: Assign the preset proportional coefficient and the preset integral coefficient to the proportional adjustment coefficient and the integral adjustment coefficient respectively.

[0108] When the charge feedback control circuit 413 determines that the currently obtained level change error value Ver is within the preset error threshold range, it assigns the preset proportional coefficient kp0 and the preset integral coefficient ki0 to the proportional adjustment coefficient kpt and the integral adjustment coefficient kit respectively, that is, maintains the current PI parameters unchanged and is the PI reference value, and makes the proportional adjustment coefficient kpt equal to the preset proportional coefficient kp0, and the integral adjustment coefficient kit equal to the preset integral coefficient ki0.

[0109] S1636: Multiply the preset proportional coefficient by a second proportional decreasing factor to obtain a proportional adjustment coefficient.

[0110] When the charge feedback control circuit 413 determines that the currently obtained level change error value Ver is less than the preset error threshold range, it multiplies the preset proportionality coefficient kp0 by the second proportionality decreasing factor bj2 to obtain the proportional regulation coefficient kpt, that is, kpt = kp0 * bj2.

[0111] S1637: Multiply the preset integral coefficient by the second integral decreasing factor to obtain the integral regulation coefficient.

[0112] The charge feedback control circuit 413 multiplies the preset integral coefficient ki0 by the second integral decreasing factor jj2 to obtain the integral regulation coefficient kit, that is, kit = ki0 * jj2.

[0113] In some embodiments, when the currently obtained level change error value Ver is the same, the second proportionality decreasing factor bj2 is different from the second proportionality increasing factor bs2, and the second integral decreasing factor jj2 is different from the second integral increasing factor js2.

[0114] In some embodiments, the second proportionality increasing factor bs2 and the second integral increasing factor js2 may be the same or different; and the second proportionality increasing factor bs2 and the second integral increasing factor js2 can respectively respond to the amplitude change of the pulse reference signal Iref, that is, they are different or the same according to the difference between the level amplitude before the step change of the pulse reference signal Iref and the level amplitude after the step change, and can be specifically obtained by fitting and setting according to simulation prediction or experimental optimization. This application does not make any limitations in this regard.

[0115] It can be understood that the charge feedback control circuit 413 is also used to integrate the pulse reference signal Iref within one period to obtain the corresponding target charge amount Qref, and subtract the charge integration amount Qphase from the target charge amount Qref to calculate the error between the actual charge and the target charge, that is, the charge error value Qer.

[0116] Furthermore, the charge feedback control circuit 413 uses the currently updated proportional regulation coefficient kpt and integral regulation coefficient kit to perform proportional-integral regulation on the charge error value Qer to output a reference signal for modulating the duty cycle, that is, the drive control signal PWM, and sends the drive control signal PWM to the first upper switch tube Q H 1 and the first lower switch tube Q L 1 respectively, so as to adjust the output current Io.

[0117] And when the second voltage conversion circuit 50 is a multi-phase BUCK circuit, the charge feedback control circuit 413 is used to send the drive control signal PWM to the first upper switch tube Q H 1 and the second upper switch tube Q H2, ..., the n-th upper switching transistor Q H n, the first lower switching transistor Q L 1, the second lower switching transistor Q L 2, ..., the n-th lower switching transistor Q L n, to adjust the output current Io.

[0118] It can be understood that through the above method, the charge feedback control circuit 413 can dynamically adjust the duty cycle of the drive control signal PWM. For the rising and falling stages of the pulse reference signal Iref, it can quickly and stably respond to the sudden change of the output current Io, so that the second voltage conversion circuit 50 has a sufficiently short current rise time and fall time.

[0119] It should be noted that the drive control signals PWM received by different switching transistors are different and there is a specific phase difference, which will not be elaborated here.

[0120] Furthermore, in an embodiment, S1632 may specifically further include: detecting whether the absolute value of the level change error value Ver is greater than the error preset value, and detecting whether the level change error value Ver is greater than zero.

[0121] It can be understood that the error preset value is the upper limit value of the preset error threshold range, that is, 5%-10% of the maximum value of the pulse reference signal Iref, and preferably 6% of the maximum value of the pulse reference signal Iref.

[0122] Wherein, if the absolute value of the level change error value Ver is greater than the error preset value and greater than zero, then execute S1633; if the absolute value of the level change error value Ver is less than or equal to the error preset value, then execute S1635; if the absolute value of the level change error value Ver is greater than the error preset value and less than zero, then execute S1637.

[0123] Please continue to refer to Figure 8 , Figure 8 is Figure 5 a schematic flowchart of an embodiment of S1633. In an embodiment, the power supply control method of the present application further includes some more specific steps in addition to the above S1631-S1637. Specifically, S1633 may specifically further include the following steps: S16331: Obtain a proportional rising correction factor using the level change error value.

[0124] It is understandable that when the step change amplitude of the pulse reference signal Iref, that is, the level change error value Ver, is different, different PI control parameters will be corresponding. After adjusting the preset proportional coefficient kp0 and the preset integral coefficient ki0 in response to the rise or fall of the pulse reference signal Iref, it is also necessary to further correct according to different level change error values Ver.

[0125] Specifically, the charge feedback control circuit 413 calculates or looks up a preset mapping relationship table according to the currently obtained level change error value Ver to obtain a proportional rise correction factor bsz.

[0126] In some embodiments, the proportional rise correction factor bsz is positively correlated with the level change error value Ver, that is, when the level change error value Ver is larger, the proportional rise correction factor bsz is also larger; when the level change error value Ver is smaller, the proportional rise correction factor bsz is also smaller; and the proportional rise correction factor bsz can specifically have any reasonable positive proportional relationship with the level change error value Ver, such as a linear function, a first-order non-linear function, a second-order non-linear function, an arithmetic function, or a specific mapping relationship, etc. The present application does not limit this.

[0127] S16332: After multiplying the preset proportional coefficient by the second proportional rise factor, then multiplying by the proportional rise correction factor to obtain a proportional adjustment coefficient.

[0128] The charge feedback control circuit 413 multiplies the preset proportional coefficient kp0 by the second proportional rise factor bs2, and then multiplies by the proportional rise correction factor bsz to obtain a proportional adjustment coefficient kpt, that is, kpt = kp0 * bs2 * bsz.

[0129] Furthermore, in one embodiment, the above S16331 may specifically further include: performing arithmetic processing on the level change error value Ver using a preset correction function or a preset mapping relationship table to obtain a proportional rise correction factor bsz.

[0130] It is understandable that the preset correction function or the preset mapping relationship table can be specifically obtained by simulation prediction or experimental optimization. The charge feedback control circuit 413 can specifically perform arithmetic processing on the level change error value Ver using the preset correction function to obtain a proportional rise correction factor bsz, or can obtain the proportional rise correction factor bsz corresponding to the level change error value Ver by looking up the preset mapping relationship table.

[0131] Please continue to refer to Figure 9 , Figure 9 is Figure 5Flow schematic diagram of an embodiment of S1634. In one embodiment, in addition to the above S1631 - S1637, the power control method of the present application further includes some more specific steps. Specifically, the above S1634 may further specifically include the following steps: S16341: Obtain an integral rising correction factor using the level change error value.

[0132] Similarly, the charge feedback control circuit 413 is also used to calculate or look up a preset mapping relationship table according to the currently obtained level change error value Ver to obtain the integral rising correction factor jsz.

[0133] In some embodiments, the integral rising correction factor jsz is positively correlated with the level change error value Ver, that is, when the level change error value Ver is larger, the integral rising correction factor jsz is also larger; when the level change error value Ver is smaller, the integral rising correction factor jsz is also smaller; and the integral rising correction factor jsz can specifically have any reasonable positive proportional relationship with the level change error value Ver such as a linear function, a first - order non - linear function, a second - order non - linear function, an arithmetic function, or a specific mapping relationship, and the present application does not limit this.

[0134] S16342: Multiply the preset integral coefficient by the second integral rising factor, and then multiply by the integral rising correction factor to obtain the integral adjustment coefficient.

[0135] The charge feedback control circuit 413 multiplies the preset integral coefficient ki0 by the second integral rising factor js2, and then multiplies by the integral rising correction factor jsz to obtain the integral adjustment coefficient kit, that is, kit = ki0 * js2 * jsz.

[0136] Further, in one embodiment, the above S16341 may further specifically include: performing arithmetic processing on the level change error value Ver using a preset correction function or a preset mapping relationship table to obtain the integral rising correction factor jsz.

[0137] It can be understood that the preset correction function or the preset mapping relationship table can be specifically obtained by simulation prediction or experimental optimization for fitting. The charge feedback control circuit 413 can specifically perform arithmetic processing on the level change error value Ver using the preset correction function to obtain the integral rising correction factor jsz, or can also obtain the integral rising correction factor jsz corresponding to the level change error value Ver by looking up the preset mapping relationship table.

[0138] Please continue to refer to Figure 10 , Figure 10 is Figure 5Flow diagram of an embodiment of S1636. In one embodiment, in addition to the above S1631 - S1637, the power control method of the present application further includes some more specific steps. Specifically, the above S1636 may further include the following steps: S16361: Obtain a proportional reduction correction factor using the level change error value.

[0139] Similarly, the charge feedback control circuit 413 is further configured to calculate or look up a preset mapping relationship table according to the currently obtained level change error value Ver to obtain a proportional reduction correction factor bjz.

[0140] In some embodiments, the proportional reduction correction factor bjz is positively correlated with the level change error value Ver, and the proportional reduction correction factor bjz may specifically have any reasonable proportional relationship with the level change error value Ver, such as a linear function, a first - order non - linear function, a second - order non - linear function, an arithmetic function, or a specific mapping relationship, and the present application does not limit this.

[0141] S16362: Multiply the preset proportional coefficient by the second proportional reduction factor and then by the proportional reduction correction factor to obtain a proportional adjustment coefficient.

[0142] The charge feedback control circuit 413 multiplies the preset proportional coefficient kp0 by the second proportional reduction factor bj2 and then by the proportional reduction correction factor bjz to obtain a proportional adjustment coefficient kpt, that is, kpt = kp0 * bj2 * bjz.

[0143] Further, in one embodiment, the above S16361 may further include: performing arithmetic processing on the level change error value Ver using a preset correction function or a preset mapping relationship table to obtain a proportional reduction correction factor bjz.

[0144] It can be understood that the preset correction function or the preset mapping relationship table can be specifically obtained by simulation prediction or experimental optimization fitting. The charge feedback control circuit 413 can specifically perform arithmetic processing on the level change error value Ver using the preset correction function to obtain a proportional reduction correction factor bjz, or can obtain the proportional reduction correction factor bjz corresponding to the level change error value Ver by looking up the preset mapping relationship table.

[0145] Please continue to refer to Figure 11 , Figure 11 is Figure 5 Flow diagram of an embodiment of S1637. In one embodiment, in addition to the above S1631 - S1637, the power control method of the present application further includes some more specific steps. Specifically, the above S1637 may further include the following steps: S16371: Obtain the integral decrease correction factor using the level change error value.

[0146] Similarly, the charge feedback control circuit 413 is further configured to calculate or look up a preset mapping relationship table according to the currently obtained level change error value Ver to obtain the integral decrease correction factor jjz.

[0147] In some embodiments, the integral decrease correction factor jjz is positively correlated with the level change error value Ver, and the integral decrease correction factor jjz may specifically have any reasonable proportional relationship with the level change error value Ver, such as a linear function, a first-order non-linear function, a second-order non-linear function, an arithmetic function, or a specific mapping relationship, etc. The present application does not make any limitations in this regard.

[0148] S16372: Multiply the preset integral coefficient by the second integral decrease factor and then multiply by the integral decrease correction factor to obtain the integral adjustment coefficient.

[0149] The charge feedback control circuit 413 multiplies the preset integral coefficient ki0 by the second integral decrease factor jj2 and then multiplies by the integral decrease correction factor jjz to obtain the integral adjustment coefficient kit, that is, kit = ki0 * jj2 * jjz.

[0150] Further, in one embodiment, the above S16371 may specifically further include: performing arithmetic processing on the level change error value Ver using a preset correction function or a preset mapping relationship table to obtain the integral decrease correction factor jjz.

[0151] It can be understood that the preset correction function or the preset mapping relationship table can be specifically obtained by simulation prediction or experimental optimization. The charge feedback control circuit 413 can specifically perform arithmetic processing on the level change error value Ver using the preset correction function to obtain the integral decrease correction factor jjz, or can obtain the integral decrease correction factor jjz corresponding to the level change error value Ver by looking up the preset mapping relationship table.

[0152] In some embodiments, when the currently obtained level change error value Ver is the same, the proportional decrease correction factor bjz is different from the proportional increase correction factor bsz, and the integral decrease correction factor jjz is different from the integral increase correction factor jsz.

[0153] Please continue to refer to Figure 12 , Figure 12 is Figure 1 a schematic flowchart of an embodiment of S17. In one embodiment, the power supply control method of the present application further includes some more specific steps in addition to the above S11 - S18. Specifically, the above S17 may specifically further include the following steps: S171: Obtain the output current.

[0154] Specifically, the first power control circuit 20 is configured to sample and obtain its output current Io from the first voltage conversion circuit 30.

[0155] S172: Subtract the output current from the pulse reference signal to obtain a current error value.

[0156] Subtract the output current Io from the pulse reference signal Iref to calculate the current error value Ier, i.e., Ier = Iref - Io.

[0157] S173: Obtain a proportional control factor coefficient and an integral control factor coefficient using the current error value.

[0158] It can be understood that when the difference between the pulse reference signal Iref and the output current Io, i.e., the current error value Ier, is different, in order to ensure good current rise time and current fall time, different PI control parameters will also be corresponding. For example, for a single pulse rise stage or pulse fall stage, the proportional control factor coefficient bk0 and the integral control factor coefficient jk0 are time-varying. For the rise stage of the pulse reference signal Iref, at the initial moment, the difference between the pulse reference signal Iref and the output current Io is large, that is, the current error value Ier is large. In order to make the output current Io quickly approach the pulse reference signal Iref, a larger proportional control factor coefficient bk0 and integral control factor coefficient jk0 need to be set to obtain the optimal current rise time effect; while at the end of the pulse step, the difference between the pulse reference signal Iref and the output current Io is small, that is, the current error value Ier is small, and a smaller proportional adjustment coefficient kpt and integral adjustment coefficient kit need to be set so that the current output current Io can reach the pulse reference signal Iref through fine-tuning, thereby avoiding unnecessary current overshoot.

[0159] Therefore, after adjusting the preset proportional coefficient kp0 and the preset integral coefficient ki0 in response to the rise or fall of the pulse reference signal Iref, it is also necessary to further adjust according to different current error values Ier.

[0160] Specifically, the first power control circuit 20 performs corresponding function calculations or looks up a mapping relationship table on the currently obtained current error value Ier to obtain a proportional control factor coefficient bk0 and an integral control factor coefficient jk0.

[0161] In some embodiments, both the proportional control factor coefficient bk0 and the integral control factor coefficient jk0 are positively correlated with the current error value Ier. That is, when the current error value Ier is large, the proportional control factor coefficient bk0 and the integral control factor coefficient jk0 are also large; when the current error value Ier is small, the proportional control factor coefficient bk0 and the integral control factor coefficient jk0 are also small; and the proportional control factor coefficient bk0 and the integral control factor coefficient jk0 can specifically have any reasonable positive proportional relationship with the current error value Ier, such as a linear function, a first-order non-linear function, a second-order non-linear function, an arithmetic function, or a specific mapping relationship, etc. The present application does not limit this.

[0162] S174: Multiply the proportional adjustment coefficient by the proportional control factor coefficient to obtain the proportional control coefficient.

[0163] Multiply the proportional adjustment coefficient kpt by the proportional control factor coefficient bk0 to obtain the proportional control coefficient kpz, that is, kpz = kpt * bk0.

[0164] S175: Multiply the integral adjustment coefficient by the integral control factor coefficient to obtain the integral control coefficient.

[0165] Multiply the integral adjustment coefficient kit by the integral control factor coefficient jk0 to obtain the integral control coefficient kiz, that is, kiz = kit * jk0.

[0166] S176: Use the proportional control coefficient and the integral control coefficient to perform proportional-integral adjustment on the charge error value to obtain the drive control signal.

[0167] Use the updated proportional control coefficient kpz and the integral control coefficient kiz to perform proportional-integral adjustment on the charge error value Qer to update the reference signal of the output modulation duty cycle, that is, the drive control signal PWM.

[0168] Please continue to refer to Figure 13 , Figure 13 Yes Figure 12 is a schematic flowchart of an embodiment of S174 in S1741: In response to an increase in the current error value, multiply the proportional adjustment coefficient by the rising proportional control factor coefficient to obtain the rising proportional control coefficient.

[0169] It is understandable that in some application scenarios, to ensure better power supply quality, the increase and decrease of the amplitude of the pulse reference signal Iref will correspond to different PI parameters. Therefore, after obtaining the level change error value Ver, it is necessary to further determine the positive and negative values to distinguish it, so as to determine the current change trend of the pulse reference signal Iref.

[0170] Among them, the proportional control factor coefficient bk0 further includes a rising proportional control factor coefficient sbk and a falling proportional control factor coefficient jbk, and the proportional control coefficient kpz includes a rising proportional control coefficient skpz and a falling proportional control coefficient jkpz.

[0171] Specifically, the first power control circuit 20 detects the current error value Ier in real time. When it is determined that the current error value Ier increases, the proportional adjustment coefficient kpt is multiplied by the rising proportional control factor coefficient sbk to obtain the rising proportional control coefficient skpz, that is, skpz = kpt * sbk * kpz.

[0172] S1742: In response to the decrease of the current error value, multiply the proportional adjustment coefficient by the falling proportional control factor coefficient to obtain the falling proportional control coefficient.

[0173] When it is determined that the current error value Ier decreases, the proportional adjustment coefficient kpt is multiplied by the falling proportional control factor coefficient jbk to obtain the falling proportional control coefficient jkpz, that is, kpz = kpt * jbk.

[0174] Among them, when the currently obtained current error value Ier is the same, the falling proportional control factor coefficient jbk is different from the rising proportional control factor coefficient sbk.

[0175] Please continue to refer to Figure 14 , Figure 14 is Figure 12 a schematic flowchart of an embodiment of S175 in. In an embodiment, the power control method of the present application further includes some more specific steps in addition to the above S171 - S176. Specifically, the above S175 may further include the following steps: S1751: In response to the increase of the current error value, multiply the integral adjustment coefficient by the rising integral control factor coefficient to obtain the rising integral control coefficient.

[0176] Among them, the integral control factor coefficient jk0 further includes a rising integral control factor coefficient sjk and a falling integral control factor coefficient jjk, and the integral control coefficient kiz includes a rising integral control coefficient skiz and a falling integral control coefficient jkiz.

[0177] Similarly, when it is determined that the current error value Ier increases, the integral regulation coefficient kit is multiplied by the rising integral control factor coefficient sjk to obtain the rising integral control coefficient skiz, that is, kiz = kit * sjk.

[0178] S1752: In response to a decrease in the current error value, multiply the integral regulation coefficient by the falling integral control factor coefficient to obtain the falling integral control coefficient.

[0179] When it is determined that the current error value Ier decreases, the integral regulation coefficient kit is multiplied by the falling integral control factor coefficient jjk to obtain the falling integral control coefficient jkiz, that is, kiz = kit * jjk.

[0180] Among them, when the currently obtained current error value Ier is the same, the falling integral control factor coefficient jjk is different from the rising integral control factor coefficient sjk.

[0181] In some embodiments, the rising ratio control factor coefficient sbk and the rising integral control factor coefficient sjk may specifically be the same or different; and the rising ratio control factor coefficient sbk and the rising integral control factor coefficient sjk may respectively be different or the same in response to different current error values Ier, and are obtained by fitting and setting according to simulation prediction or experimental optimization. The present application does not make any limitations in this regard.

[0182] In some embodiments, the falling ratio control factor coefficient jbk and the falling integral control factor coefficient jjk may specifically be the same or different; and the falling ratio control factor coefficient jbk and the falling integral control factor coefficient jjk may respectively be different or the same in response to different current error values Ier, and are obtained by fitting and setting according to simulation prediction or experimental optimization. The present application does not make any limitations in this regard.

[0183] The present application also provides an electronic device. Please refer to Figure 15 , Figure 15 which is a schematic structural diagram of an embodiment of the electronic device of the present application. In this embodiment, the electronic device 60 includes a housing 61 and a third power supply control circuit 62 connected to the housing 61.

[0184] It should be noted that the third power supply control circuit 62 described in this embodiment is the first power supply control circuit 20 or the second power supply control circuit 40 described in any one of the above embodiments. For details, please refer to Figures 1 - 14 and the relevant text content, which will not be elaborated here.

[0185] The beneficial effects of the present application are as follows: Different from the prior art, the power control method provided by the present application obtains the instantaneous value of the conduction current in the voltage conversion circuit, integrates the instantaneous value of the conduction current to obtain the charge integration amount, and obtains the pulse reference signal, the preset proportional coefficient, and the preset integration coefficient, so as to convert the pulse reference signal into the target charge amount. The target charge amount is subtracted from the charge integration amount to obtain the charge error value. When the level amplitude of the pulse reference signal changes, the preset proportional coefficient and the preset integration coefficient are respectively adjusted to obtain the proportional adjustment coefficient and the integration adjustment coefficient, so as to perform proportional-integral adjustment on the charge error value by using the proportional adjustment coefficient and the integration adjustment coefficient to obtain the drive control signal. Therefore, it can respond to the change in the level amplitude of the pulse reference signal, that is, when the load state changes, by adjusting the preset proportional coefficient and the preset integration coefficient, the obtained drive control signal can more quickly adjust the output current of the voltage conversion circuit to the current amplitude range required by the changed load state, effectively reducing the rise time and fall time of the output current, thereby achieving fast response in the full load range; and there is no need to make the corresponding power device work in the linear region, the power loss is low, the reliability is good, and the output power does not need to be limited.

[0186] The above are only the embodiments of the present application, and do not limit the patent scope of the present application. Any equivalent structure or equivalent process transformation made by using the content of the specification and drawings of the present application, or directly or indirectly applied in other related technical fields, shall be equally included in the patent protection scope of the present application.

Claims

1. A power control method, applied to the power control of a voltage conversion circuit, characterized in that The power control method includes: Obtaining the instantaneous value of the conduction current in the voltage conversion circuit; Performing an integration process on the instantaneous value of the conduction current to obtain a charge integration amount; Obtaining a pulse reference signal, a preset proportional coefficient, and a preset integration coefficient; Converting the pulse reference signal into a target charge amount; Subtracting the charge integration amount from the target charge amount to obtain a charge error value; Adjusting the preset proportional coefficient and the preset integration coefficient respectively in response to the change in the level amplitude of the pulse reference signal to obtain a proportional adjustment coefficient and an integral adjustment coefficient; wherein, the step of adjusting the preset proportional coefficient and the preset integration coefficient respectively in response to the change in the level amplitude of the pulse reference signal to obtain a proportional adjustment coefficient and an integral adjustment coefficient includes: obtaining the level change error value of the pulse reference signal; detecting whether the level change error value is within a preset error threshold range; if the level change error value is greater than the preset error threshold range; multiplying the preset proportional coefficient by a second proportional increase factor to obtain the proportional adjustment coefficient; multiplying the preset integration coefficient by a second integral increase factor to obtain the integral adjustment coefficient; Performing a proportional-integral adjustment on the charge error value by using the proportional adjustment coefficient and the integral adjustment coefficient to obtain a drive control signal; Sending the drive control signal to the voltage conversion circuit to trigger the voltage conversion circuit to change the switch state, thereby adjusting the output current of the voltage conversion circuit.

2. The power control method according to claim 1, wherein The step of adjusting the preset proportional coefficient and the preset integration coefficient respectively in response to the change in the level amplitude of the pulse reference signal to obtain a proportional adjustment coefficient and an integral adjustment coefficient includes: Obtaining the rising edge of the pulse reference signal; Multiplying the preset proportional coefficient by a first proportional increase factor in response to the rising edge to obtain the proportional adjustment coefficient; Multiplying the preset integration coefficient by a first integral increase factor to obtain the integral adjustment coefficient.

3. The power control method according to claim 1, wherein The step of adjusting the preset proportional coefficient and the preset integration coefficient in response to the change in the level amplitude of the pulse reference signal to obtain a proportional adjustment coefficient and an integral adjustment coefficient includes: Obtaining the falling edge of the pulse reference signal; Multiplying the preset proportional coefficient by a first proportional decrease factor in response to the falling edge to obtain the proportional adjustment coefficient; Multiplying the preset integration coefficient by a first integral decrease factor to obtain the integral adjustment coefficient.

4. The power control method according to claim 1, wherein The step of multiplying the preset proportional coefficient by a second proportional increase factor to obtain the proportional adjustment coefficient includes: Obtaining a proportional increase correction factor by using the level change error value; wherein, the proportional increase correction factor is positively correlated with the level change error value; After multiplying the preset proportional coefficient by the second proportional increase factor, multiplying the result by the proportional increase correction factor to obtain the proportional adjustment coefficient.

5. The power control method according to claim 4, wherein The step of obtaining a proportional increase correction factor by using the level change error value includes: Performing an arithmetic process on the level change error value by using a preset correction function or a preset mapping relationship table to obtain the proportional increase correction factor.

6. The power control method according to claim 4, characterized in that, The step of multiplying the preset integral coefficient by the second integral rising factor to obtain the integral adjustment coefficient includes: Obtaining an integral rising correction factor by using the level change error value; wherein, the integral rising correction factor is positively correlated with the level change error value; After multiplying the preset integral coefficient by the second integral rising factor, multiplying the result by the integral rising correction factor to obtain the integral adjustment coefficient.

7. The power control method according to claim 1, wherein The power supply control method further includes: If the level change error value is less than the preset error threshold range; Multiplying the preset proportionality coefficient by the second proportionality decreasing factor to obtain the proportionality adjustment coefficient; Multiplying the preset integral coefficient by the second integral decreasing factor to obtain the integral adjustment coefficient.

8. The power control method according to claim 7, wherein The step of multiplying the preset proportionality coefficient by the second proportionality decreasing factor to obtain the proportionality adjustment coefficient includes: Obtaining a proportionality decreasing correction factor by using the level change error value; wherein, the proportionality decreasing correction factor is positively correlated with the level change error value; After multiplying the preset proportionality coefficient by the second proportionality decreasing factor, multiplying the result by the proportionality decreasing correction factor to obtain the proportionality adjustment coefficient.

9. The power control method according to claim 8, wherein The step of multiplying the preset integral coefficient by the second integral decreasing factor to obtain the integral adjustment coefficient includes: Obtaining an integral decreasing correction factor by using the level change error value; wherein, the integral decreasing correction factor is positively correlated with the level change error value; After multiplying the preset integral coefficient by the second integral decreasing factor, multiplying the result by the integral decreasing correction factor to obtain the integral adjustment coefficient.

10. The power control method according to any one of claims 1-9, characterized in that, The step of performing proportional-integral adjustment on the charge error value by using the proportionality adjustment coefficient and the integral adjustment coefficient to obtain a drive control signal includes: Obtaining the output current; Subtracting the output current from the pulse reference signal to obtain a current error value; Obtaining a proportional control factor coefficient and an integral control factor coefficient by using the current error value; wherein, both the proportional control factor coefficient and the integral control factor coefficient are positively correlated with the current error value; Multiplying the proportionality adjustment coefficient by the proportional control factor coefficient to obtain a proportional control coefficient; Multiplying the integral adjustment coefficient by the integral control factor coefficient to obtain an integral control coefficient; Performing proportional-integral adjustment on the charge error value by using the proportional control coefficient and the integral control coefficient to obtain the drive control signal.

11. The power control method according to claim 10, characterized in that, The proportional control factor coefficient includes a rising proportional control factor coefficient and a falling proportional control factor coefficient, the proportional control coefficient includes a rising proportional control coefficient and a falling proportional control coefficient, and the step of multiplying the proportionality adjustment coefficient by the proportional control factor coefficient to obtain the proportional control coefficient includes: In response to an increase in the current error value, multiplying the proportionality adjustment coefficient by the rising proportional control factor coefficient to obtain the rising proportional control coefficient; In response to a decrease in the current error value, multiplying the proportionality adjustment coefficient by the falling proportional control factor coefficient to obtain the falling proportional control coefficient.

12. The power control method according to claim 10, characterized in that, The integral control factor coefficients include an increasing integral control factor coefficient and a decreasing integral control factor coefficient. The integral control coefficients include an increasing integral control coefficient and a decreasing integral control coefficient. The step of multiplying the integral adjustment coefficient by the integral control factor coefficient to obtain the integral control coefficient includes: In response to an increase in the current error value, multiplying the integral adjustment coefficient by the increasing integral control factor coefficient to obtain the increasing integral control coefficient; In response to a decrease in the current error value, multiplying the integral adjustment coefficient by the decreasing integral control factor coefficient to obtain the decreasing integral control coefficient.

13. A power control circuit, characterized in that, The power supply control circuit is coupled to the voltage conversion circuit; Wherein, the power supply control circuit performs power supply control on the voltage conversion circuit by using the power supply control method described in any one of claims 1-12.

14. An electronic device, characterized in that, The electronic device includes a housing and a power supply control circuit connected to the housing; Wherein, the power supply control circuit is the power supply control circuit described in claim 13.

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