Dual launch compact underwater wireless power transfer system
By designing a compact magnetic coupling structure with dual launchers, the problem of poor anti-deviation performance of underwater wireless power transmission systems in complex seabed environments has been solved, achieving more efficient energy exchange and longer endurance for autonomous underwater vehicles.
Patent Information
- Authority / Receiving Office
- CN · China
- Patent Type
- Patents(China)
- Current Assignee / Owner
- HARBIN INST OF TECH
- Filing Date
- 2025-12-08
- Publication Date
- 2026-04-10
AI Technical Summary
Existing underwater wireless power transfer systems have poor anti-drift performance in complex seabed environments, resulting in reduced energy exchange efficiency and stability, which affects the endurance and charging efficiency of autonomous underwater vehicles.
It adopts a dual-transmitter compact magnetic coupling structure, including a main transmitting coil, an integrated reverse transmitting coil, a ferrite core and a receiving coil. Through magnetic field superposition and orthogonal winding design, the system’s anti-offset performance and lightweight characteristics are improved.
It effectively reduces mutual inductance changes under offset conditions, improves the stability and transmission efficiency of the wireless power transmission system, and enhances the endurance and charging stability of autonomous underwater vehicles.
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Figure CN121283050B_ABST
Abstract
Description
TECHNICAL FIELD
[0001] The application relates to a double-transmitting compact underwater wireless power transmission system and belongs to the technical field of underwater wireless power transmission. BACKGROUND
[0002] Establishing a marine scientific observation system is an effective way to detect and develop and utilize the ocean, and an autonomous underwater vehicle is an important mobile observation device in the marine observation system. With the steady improvement of the performance of the autonomous underwater vehicle, the scope and depth of operation and application are continuously expanding. Limited by the current energy supply level, the autonomous underwater vehicle has a short single endurance time, and it is difficult to meet the demand for long-term operation in complex marine environments. Therefore, how to achieve efficient and stable power supply is one of the key problems restricting the cruising capability of the autonomous underwater vehicle.
[0003] Compared with the traditional wet-plug underwater power supply mode, the wireless power transmission does not require wires or other physical connections to complete power supply to the equipment, has the advantages of good insulation, simple structure, high safety, convenient operation, and strong concealment; in addition, compared with the manual battery replacement mode, the wireless power transmission technology avoids the size and weight constraints of the battery, can carry a larger capacity battery pack, improves the single endurance time, reduces the necessary floating time for manual battery replacement, and can perform charging operations on the seabed, thereby improving the charging efficiency of the autonomous underwater vehicle. Therefore, the wireless power transmission technology has good application prospects in the power supply of intelligent marine equipment such as autonomous underwater vehicles (AUVs).
[0004] The wireless power transmission technology is currently widely used in electric vehicles, smart wearable devices, and implantable medical devices. For example, in the application of electric vehicles, the wireless power transmission technology can realize non-contact charging of the vehicle under static or dynamic conditions, avoiding the problem that the traditional wired charging interface is easily damaged in harsh environments such as moisture and corrosion; in the application of smart wearable devices such as smartphones and earphones, the wireless power transmission technology can improve the endurance of the devices and reduce the damage to the devices caused by frequent replacement or plugging of the charging interface; in implantable medical devices, wireless energy transmission can effectively solve the problem of difficult battery replacement in the body, thereby significantly reducing the surgical risk of patients and improving the stability and safety of medical devices.
[0005] For a wireless power transmission system, stable energy exchange between the transmitting device and the receiving device is the core approach to energy transmission. However, in the complex environment of the seabed, the device offset caused by ocean current fluctuations can cause the energy exchange unit to deviate from the optimal coupling position, thereby causing the system coupling performance to decline, affecting the power transmission efficiency and stability. Therefore, improving the anti-offset performance of the wireless power transmission system is an important means to improve the system efficiency.
[0006] In the underwater wireless power transmission system, the magnetic coupler is a key component to realize energy transmission, and its structure and performance directly determine the transmission power and efficiency of the system. However, due to the limited internal space of the AUV, strict requirements are put forward for the volume, weight and geometric structure of the receiving device. The existing magnetic coupling mechanism applied to the AUV only considers the coupling performance under the condition of directly facing and slight deviation, and when the deviation is large, the overall efficiency of the system will be significantly affected; in addition, the existing magnetic coupling mechanism uses a single coil as the transmitting unit, and the magnetic field distribution is relatively single, and the receiving end compensation device uses an independent magnetic flux loop, which needs additional space for installation, increasing the volume and weight of the AUV. SUMMARY
[0007] In view of the poor anti-deviation performance of the existing magnetic coupling mechanism, the application provides a double-transmitting compact underwater wireless power transmission system.
[0008] The double-transmitting compact underwater wireless power transmission system provided by the application comprises a magnetic coupling structure.
[0009] The magnetic coupling structure comprises a main transmitting coil L P1 , an integrated reverse transmitting coil L P2 , a ferrite core, a receiving coil L S and a receiving-side integrated inductance coil L S1 .
[0010] The main transmitting coil L P1 , the integrated reverse transmitting coil L P2 and the ferrite core are sequentially arranged from inside to outside on the outside of the vehicle hull; and the main transmitting coil L P1 and the ferrite core have the same curvature;
[0011] The receiving coil L S is horizontally fixed in the vehicle hull and is square-wound; the receiving-side integrated inductance coil L S1 is square-wound and is centrally and orthogonally wound on the receiving coil L S .
[0012] The main transmitting coil L P1 , the integrated reverse transmitting coil L P2 and the ferrite core are aligned at the center and are concentrically arranged to form a transmitting-side coil; the receiving coil L S and the receiving-side integrated inductance coil L S1 form a receiving-side coil; and the centers of the transmitting-side coil and the receiving-side coil are aligned.
[0013] It also comprises a transmitting end and a receiving end based on the magnetic coupling structure.
[0014] The transmitting end comprises a direct current voltage source U DC , a voltage type inverter, a transmitting end inductor coil L Pf , a parallel compensation capacitor C Pf , a series compensation capacitor C P , a main transmitting coil L P1 and an integrated reverse transmitting coil L P2 ; the voltage type inverter comprises a switch tube Q1, a switch tube Q2, a switch tube Q3 and a switch tube Q4;
[0015] The source of the switch tube Q1 is connected to the drain of the switch tube Q2, the source of the switch tube Q2 is connected to the source of the switch tube Q4, the drain of the switch tube Q4 is connected to the source of the switch tube Q3, the drain of the switch tube Q3 is connected to the drain of the switch tube Q1; the drain of the switch tube Q1 is connected to the positive pole of the direct current voltage source U DC , and the negative pole of the direct current voltage source U DC is connected to the source of the switch tube Q2;
[0016] The source of the switch tube Q1 is connected to one end of the transmitting end inductor coil L Pf , the other end of the transmitting end inductor coil L Pf is connected to one end of the parallel compensation capacitor C Pf , the other end of the parallel compensation capacitor C Pf is connected to the drain of the switch tube Q4; the other end of the transmitting end inductor coil L Pf is connected to one end of the series compensation capacitor C P , the other end of the series compensation capacitor C P is connected to the same-named end of the main transmitting coil L P1 , the different-named end of the main transmitting coil L P1 is connected to the different-named end of the integrated reverse transmitting coil L P2 , and the same-named end of the integrated reverse transmitting coil L P2 is connected to the other end of the parallel compensation capacitor C Pf ;
[0017] The receiving end comprises a receiving coil L S , a series compensation capacitor C S , a parallel compensation capacitor C S1 , a receiving side integrated inductor coil L S1 , a rectifier, a filter capacitor C out and a battery load R L ; the rectifier comprises a diode D5, a diode D6, a diode D7 and a diode D8;
[0018] The same-named end of the receiving coil L S corresponds to the same-named end of the main transmitting coil L P1 , and the same-named end of the receiving coil L S is connected to the series compensation capacitor C SOne end of the series compensation capacitor C S The other end of the parallel compensation capacitor C S1 One end of the parallel compensation capacitor C S1 The other end of the parallel compensation capacitor C S The opposite end of the receiving coil L S One end of the receiving side integrated inductor coil L S1 The other end of the receiving side integrated inductor coil L S1 The anode of diode D5 is connected to the other end of the receiving coil L S The opposite end of the receiving coil L out The filter capacitor C L Is connected between the cathode of diode D7 and the anode of diode D8, and the battery load R out In parallel with the filter capacitor C
[0019] The beneficial effects of the present application: the present application improves the anti-deviation performance of the bidirectional wireless power transmission system and achieves the lightweight target by designing a double transmitting coil based magnetic integrated coupling structure for underwater vehicles. Due to the appropriate transmission distance between the transmitting and receiving units, the entire wireless power supply system has good coupling and anti-deviation performance.
[0020] The magnetic coupling mechanism of the present application adopts double transmitting coils, which can reduce the mutual inductance change caused by deviation through the method of magnetic field superposition, thereby achieving the purpose of anti-deviation and suppressing output power fluctuation; through the orthogonal winding of the receiving side coil, self-decoupling and lightweight design of AUV are realized, which is beneficial to improve the endurance of AUV; through the establishment of an equivalent circuit model suitable for the magnetic coupling structure and reasonable parameter design, the reliable and stable charging of the system can be realized. BRIEF DESCRIPTION OF DRAWINGS
[0021] Figure 1 is a three-dimensional structure schematic diagram of the magnetic coupling structure of the double transmitting compact underwater wireless power transmission system of the present application;
[0022] Figure 2 is a front view of Figure 1 ;
[0023] Figure 3 is a circuit structure schematic diagram of the double transmitting compact underwater wireless power transmission system of the present application;
[0024] Figure 4 is a mutual inductance equivalent circuit diagram of Figure 3 ;
[0025] Figure 5 is the variation curve of the synthesized mutual inductance value and the coupling coefficient with the axial offset of the integrated magnetic coupling structure according to the present application when the axial offset is 0-40mm;
[0026] Figure 6 is the vector distribution diagram of the magnetic flux vector generated by the receiving coil;
[0027] Figure 7 is the vector distribution diagram of the magnetic flux vector generated by the receiving side integrated inductance coil;
[0028] Figure 8 is the magnetic field distribution diagram of the integrated magnetic coupling structure according to the present application in the directly opposite state. DETAILED DESCRIPTION
[0029] The technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application. Obviously, the described embodiments are only a part of the embodiments of the present application, rather than all the embodiments of the present application. Based on the embodiments in the present application, all other embodiments obtained by those skilled in the art without creative work fall within the scope of protection of the present application.
[0030] DETAILED DESCRIPTION Figure 1 and Figure 2 , the present application provides a double-transmit compact underwater wireless power transmission system, comprising a magnetic coupling structure.
[0031] The magnetic coupling structure comprises a main transmitting coil L P1 , an integrated reverse transmitting coil L P2 , a ferrite magnetic core, a receiving coil L S and a receiving side integrated inductance coil L S1 .
[0032] The main transmitting coil L P1 , the integrated reverse transmitting coil L P2 and the ferrite magnetic core are sequentially arranged from inside to outside on the outside of the vehicle ship body; and the arc of the main transmitting coil L P1 and the ferrite magnetic core is the same.
[0033] The receiving coil L S is square-wound and horizontally fixed in the vehicle ship body; and the receiving side integrated inductance coil L S1 is square-wound and orthogonally wound on the receiving coil L S .
[0034] The center of the main transmitting coil L P1 , the integrated reverse transmitting coil L P2 and the ferrite magnetic core is aligned, and they are concentrically arranged to form a transmitting side coil; and the receiving coil LS and receiving side integrated inductive coil L S1 form the receiving side coil; the center of the transmitting side coil and the receiving side coil are aligned.
[0035] wherein the main transmitting coil L P1 and integrated reverse transmitting coil L P2 converts the electric energy into magnetic field energy and transmits to the receiving coil L S , the receiving coil L S converts the received magnetic field energy into electric field energy and outputs to the AUV device, the ferrite core has the function of reducing magnetic field diffusion, which is beneficial to the improvement of transmission efficiency.
[0036] In this embodiment, the main transmitting coil L P1 is arc-shaped and attached to the outside of the AUV hull. The integrated reverse transmitting coil L P2 is fixed to the outside of the main transmitting coil L P1 . The receiving side integrated inductive coil L S1 is axially orthogonal to the outside of the receiving coil L S .
[0037] Further, the curvature of the integrated reverse transmitting coil L P2 is smaller than that of the main transmitting coil L P1 .
[0038] In this embodiment, the opposite end of the main transmitting coil L P1 is connected to the opposite end of the integrated reverse transmitting coil L P2 , and the phase difference between the excitation current of the main transmitting coil L P1 and the excitation current of the integrated reverse transmitting coil L P2 is 180°.
[0039] The excitation currents of the two transmitting coils are driven by the same inverter, and the excitation currents enter the main transmitting coil in the forward direction and enter the integrated reverse transmitting coil in the reverse direction, thereby realizing the phase difference of 180° between the excitation current of the main transmitting coil and the excitation current of the integrated reverse transmitting coil.
[0040] At the center of the transmitting side coil and the receiving side coil, the magnetic field vector directions of the two transmitting coils are opposite, and the mutual inductance between the two transmitting coils and the receiving coil is opposite, when axial offset and rotational offset occur, the mutual inductance between the two transmitting coils and the receiving coil is reduced at the same time, the total mutual inductance is reduced compared with the mutual inductance of single transmitting coil, thereby achieving the purpose of anti-offset and suppressing output power fluctuation.
[0041] The receiving side integrated inductive coil L S1 produces a magnetic field vector opposite to that of the receiving coil L SThe magnetic field vectors of the receiving coil L S1 and the receiving side integrated inductive coil L S are orthogonal, realizing self-decoupling and can be approximately ignored.
[0042] In this embodiment, the receiving coil L S and the receiving side integrated inductive coil L S1 have the same magnetic core. The magnetic integration of the receiving side coil has the advantage of light weight, which can minimize the impact on the long-term navigation of the AUV.
[0043] Figure 8 is the distribution diagram of the synthetic magnetic field generated by the double transmitting coils in the opposite state, Figure 8 where B represents the magnetic induction intensity, and tesla is the unit of magnetic induction intensity. When axial offset and rotational offset occur, the mutual inductance between the two transmitting coils and the receiving coil decreases, and the total mutual inductance changes compared with the mutual inductance of a single transmitting coil, thereby achieving the purpose of resisting offset and suppressing output power fluctuation.
[0044] Figure 5 is the change of the synthetic mutual inductance value and the equivalent coupling coefficient with the axial offset when the magnetic coupling mechanism has an axial offset of 0-40mm. When the axial offset occurs, the change curve of the synthetic mutual inductance value and the equivalent coupling coefficient is relatively flat, and the impact on the system is relatively small, thereby indicating that the magnetic coupling mechanism has strong anti-axial offset capability.
[0045] Figure 6 is the vector distribution diagram of the magnetic flux vector generated by the receiving coil; Figure 7 is the vector distribution diagram of the magnetic flux vector generated by the receiving side integrated inductive coil. The receiving side integrated inductive coil is axially wound outside the receiving coil, and the generated magnetic flux vector is orthogonal to the magnetic flux vectors of the transmitting side coil and the receiving coil. The magnetic flux vector generated by the receiving side integrated inductive coil hardly penetrates the transmitting side coil, and the magnetic fluxes remaining penetrating and penetrating out of the receiving coil are the same. Similarly, the magnetic flux vector generated by the receiving coil hardly penetrates the receiving side integrated inductive coil, so the mutual inductance between the receiving side integrated inductive coil and the transmitting side coil and the receiving coil can be approximately ignored. When the circuit parameters are designed, the influence of this part of mutual inductance on the working state of the system can be ignored, realizing self-decoupling.
[0046] Further, as shown in Figure 3 and Figure 4 , the double-transmitting compact underwater wireless power transmission system further comprises a transmitting end and a receiving end based on a magnetic coupling structure;
[0047] The transmitting end comprises a direct current voltage source U DC , a voltage type inverter, a transmitting end inductive coil LPf parallel compensation capacitor C Pf series compensation capacitor C P main transmitting coil L P1 and integrated reverse transmitting coil L P2 ; the voltage type inverter comprises switch tube Q1, switch tube Q2, switch tube Q3 and switch tube Q4;
[0048] The source of switch tube Q1 is connected to the drain of switch tube Q2, the source of switch tube Q2 is connected to the source of switch tube Q4, the drain of switch tube Q4 is connected to the source of switch tube Q3, and the drain of switch tube Q3 is connected to the drain of switch tube Q1; the drain of switch tube Q1 is connected to the positive pole of direct current voltage source U DC , and the negative pole of direct current voltage source U DC is connected to the source of switch tube Q2.
[0049] The source of switch tube Q1 is connected to one end of transmitting end inductance coil L Pf , the other end of transmitting end inductance coil L Pf is connected to one end of parallel compensation capacitor C Pf , the other end of parallel compensation capacitor C Pf is connected to the drain of switch tube Q4; the other end of transmitting end inductance coil L Pf is connected to one end of series compensation capacitor C P , the other end of series compensation capacitor C P is connected to the same name end of main transmitting coil L P1 , and the different name end of main transmitting coil L P1 is connected to the different name end of integrated reverse transmitting coil L P2 , and the same name end of integrated reverse transmitting coil L P2 is connected to the other end of parallel compensation capacitor C Pf .
[0050] The receiving end comprises receiving coil L S , series compensation capacitor C S , parallel compensation capacitor C S1 , receiving side integrated inductance coil L S1 , rectifier, filter capacitor C out and battery load R L ; the rectifier comprises diode D5, diode D6, diode D7 and diode D8.
[0051] The same name end of receiving coil L S corresponds to the same name end of main transmitting coil L P1 , the same name end of receiving coil L S is connected to one end of series compensation capacitor C S , and the other end of series compensation capacitor C S is connected to parallel compensation capacitor CS1 one end of the parallel compensation capacitor C S1 the other end of the parallel compensation capacitor C S the other end of the parallel compensation capacitor C S the other end of the parallel compensation capacitor C S1 the other end of the parallel compensation capacitor C S1 the anode of the diode D5, the cathode of the diode D5 connecting the cathode of the diode D7, the anode of the diode D7 connecting the cathode of the diode D8, the anode of the diode D8 connecting the anode of the diode D6, the cathode of the diode D6 connecting the anode of the diode D5; the cathode of the diode D8 connecting the opposite end of the receiving coil L S the opposite end of the receiving coil L out connected between the cathode of the diode D7 and the anode of the diode D8, the battery load R L in parallel with the filter capacitor C out .
[0052] Figure 3 In the formula, is the excitation current of the transmitting coil, is the induced current of the receiving coil, I O is the system output current, U O is the system output voltage; the working frequency of the system is f, and the angular frequency is ω = 2πf.
[0053] Figure 3 In the formula, corresponding to the switch tube Q1, the switch tube Q2, the switch tube Q3 and the switch tube Q4, the anti-parallel diodes D1, D2, D3 and D4 are respectively configured. The switch tube Q1 and Q3 are the upper bridge arm switch tubes in the inverter, and the switch tube Q2 and Q4 are the lower bridge arm switch tubes; the lead-out line at the connection point of the switch tube Q1 and the switch tube Q2 is the positive electrode of the alternating current output end, and the lead-out line at the connection point of the switch tube Q3 and the switch tube Q4 is the negative electrode of the alternating current output end. The drain of the switch tube Q1 and the switch tube Q3 in the inverter are connected to each other as the positive terminal of the inverter; the source of the switch tube Q2 and the switch tube Q4 in the inverter are connected to each other as the negative terminal of the inverter. The cathode of the diode D5 and the diode D7 in the rectifier are connected to each other as the positive terminal of the rectifier; the anode of the diode D6 and the diode D8 in the rectifier are connected to each other as the negative terminal of the rectifier.
[0054] In the embodiment, the coupling coefficient K between the transmitting side coil and the receiving side coil is :
[0055] ,
[0056] In the formula, is the combined mutual inductance value of the transmitting side coil and the receiving side coil, is the main transmitting coil LP1 and the integrated counter transmitting coil L P2 .
[0057] At the center of the transmitting side coil and the receiving coil, the magnetic field vector directions of the two transmitting coils are opposite, the mutual inductances between the two transmitting coils and the receiving coil are opposite, and the synthesized mutual inductance value is:
[0058] ,
[0059] where is the mutual inductance between the main transmitting coil L P1 and the receiving coil L S , is the mutual inductance between the integrated counter transmitting coil L P2 and the receiving coil L S .
[0060] The equivalent transmitting self-inductance is:
[0061] ,
[0062] where is the mutual inductance between the main transmitting coil L P1 and the integrated counter transmitting coil L P2 .
[0063] By the self-decoupling characteristic of the magnetic coupling structure, the mutual inductance is ignored, and the charging topology shown in Figure 3 is simplified into a mutual inductance equivalent circuit, as shown in Figure 4 , where the square wave voltage output by the inverter is approximated as a voltage source , is the output current of the inverter, R eq is the equivalent load of the rectifier and the battery load, is the input voltage of the rectifier, is the input current of the rectifier. For the theoretical feasibility of the analysis method, the power loss of the elements is ignored.
[0064] Combined with Figure 4 , according to Kirchhoff's law, we have:
[0065] ,
[0066] where is the imaginary unit.
[0067] Further, in order to improve the transmission efficiency of the system, achieve the reactive full compensation and zero phase angle impedance condition of the system, in the resonant state, according to the preset alternating current angular frequency, the corresponding circuit element parameter value is selected, and the preset alternating current angular frequency and the corresponding circuit element parameter value satisfy the following relationship:
[0068] ,
[0069] In the formula, is the preset alternating current angular frequency.
[0070] The resonant condition is substituted into the circuit equation, and the following formula can be obtained:
[0071] ,
[0072] ,
[0073] ,
[0074] ,
[0075] In the formula, is the excitation current amplitude of the transmitting coil, is the voltage source amplitude, is the system output power, is the rectifier output current amplitude, is the current gain.
[0076] According to the derived formula, under the condition that the mutual inductance between the transmitting coil and the receiving coil, the transmitting compensation inductance and the receiving compensation inductance value are known, the double-sided LCC compensation network suitable for the magnetic coupling structure can realize the constant current output independent of the load.
[0077] Although the present application is described herein with reference to particular embodiments, it is to be understood that these examples are merely hypothetical illustrations of the principles and applications of the present application. It should therefore be understood that numerous modifications can be made to the exemplary embodiments and that other arrangements can be devised without departing from the spirit and scope of the present application as defined by the appended claims. It should be understood that the features described in connection with separate embodiments can be used in combination with features described in connection with other embodiments. It should also be understood that features described in connection with individual embodiments can be used in other described embodiments.
Claims
1. A dual launch compact underwater wireless power transfer system, characterized in that, The magnetic coupling structure comprises a magnetic coupling structure; The magnetic coupling structure comprises a main transmitting coil L P1 , an integrated counter transmitting coil L P2 , a ferrite core, a receiving coil L S and a receiving-side integrated inductive coil L S1 ; wherein the main transmitting coil L P1 and the integrated counter transmitting coil L P2 are planar coils, and the receiving coil L S and the receiving-side integrated inductive coil L S1 are three-dimensional coils. The main transmitting coil L P1 , the integrated reverse transmitting coil L P2 and the ferrite core are arranged in sequence from inside to outside on the outside of the ship body of the vehicle; and the main transmitting coil L P1 and the ferrite core have the same arc. Receiving coil L S For square winding, horizontally fixed inside the aircraft hull; receiving side integrated inductor coil L S1 For square winding, horizontally fixed inside the aircraft hull; receiving side integrated inductor coil L S Upper; The main transmitting coil L P1 , the integrated reverse transmitting coil L P2 and the center of the ferrite core are aligned and arranged concentrically to form a transmitting side coil; the receiving coil L S and the receiving side integrated inductance coil L S1 form a receiving side coil; the centers of the transmitting side coil and the receiving side coil are aligned; The magnetic coupling structure comprises a magnetic coupling structure; The transmitting end comprises a direct current voltage source U DC , a voltage type inverter, a transmitting end inductor coil L Pf , a parallel compensation capacitor C Pf , a series compensation capacitor C P , a main transmitting coil L P1 and an integrated reverse transmitting coil L P2 ; the voltage type inverter comprises a switch tube Q1, a switch tube Q2, a switch tube Q3 and a switch tube Q4; The source of the switch tube Q1 is connected to the drain of the switch tube Q2, the source of the switch tube Q2 is connected to the source of the switch tube Q4, the drain of the switch tube Q4 is connected to the source of the switch tube Q3, the drain of the switch tube Q3 is connected to the drain of the switch tube Q1; the drain of the switch tube Q1 is connected to the positive pole of the direct current voltage source U DC , the negative pole of the direct current voltage source U DC is connected to the source of the switch tube Q2; The source of the switch tube Q1 is connected to one end of the transmitting end inductor coil L Pf The other end of the transmitting end inductor coil L Pf is connected to one end of the parallel compensation capacitor C Pf The other end of the parallel compensation capacitor C Pf is connected to the drain of the switch tube Q4; the other end of the transmitting end inductor coil L Pf is connected to one end of the series compensation capacitor C P The other end of the series compensation capacitor C P is connected to the same end of the main transmitting coil L P1 The different end of the main transmitting coil L P1 is connected to the different end of the integrated reverse transmitting coil L P2 The different end of the integrated reverse transmitting coil L P2 is connected to the other end of the parallel compensation capacitor C Pf ; The receiving end comprises a receiving coil L S , a series compensation capacitor C S , a parallel compensation capacitor C S1 , a receiving side integrated inductive coil L S1 , a rectifier, a filter capacitor C out and a battery load R L ; the rectifier comprises diode D5, diode D6, diode D7 and diode D8; The same name end of the receiving coil L S corresponds to the same name end of the main transmitting coil L P1 , the same name end of the receiving coil L S connects one end of the series compensation capacitor C S , the other end of the series compensation capacitor C S connects one end of the parallel compensation capacitor C S1 , the other end of the parallel compensation capacitor C S1 connects the opposite name end of the receiving coil L S ; the other end of the series compensation capacitor C S connects one end of the receiving side integrated inductance coil L S1 , the other end of the receiving side integrated inductance coil L S1 connects the anode of the diode D5, the cathode of the diode D5 connects the cathode of the diode D7, the anode of the diode D7 connects the cathode of the diode D8, the anode of the diode D8 connects the anode of the diode D6, the cathode of the diode D6 connects the anode of the diode D5; the cathode of the diode D8 connects the opposite name end of the receiving coil L S ; the filter capacitor C out is connected between the cathode of the diode D7 and the anode of the diode D8, and the battery load R L is connected in parallel with the filter capacitor C out .
2. The dual-transmit compact underwater wireless power transmission system according to claim 1, wherein, The integrated counter-emission coil L P2 has an arc length smaller than the arc length of the main emission coil L P1 .
3. The dual-transmit compact underwater wireless power transmission system according to claim 1, wherein, the main transmitting coil L P1 the opposite end of the integrated counter transmitting coil L P2 the opposite end of the integrated counter transmitting coil L P1 the phase difference of the excitation current of the main transmitting coil L P2 the integrated counter transmitting coil L 4. The dual launch compact underwater wireless power transfer system of claim 1, wherein, Receiving coil L S and the receiving side integrated inductor coil L S1 have the same magnetic core.
5. The dual-transmit compact underwater wireless power transmission system according to claim 1, wherein, The coupling coefficient between the transmit-side coil and the receive-side coil is: ， wherein is the combined mutual inductance value of the transmit side coil and the receive side coil, is the main transmit coil L P1 and the equivalent transmit self-inductance of the integrated counter transmit coil L P2 .
6. The dual-transmit compact underwater wireless power transmission system according to claim 5, wherein, Synthetic mutual inductance value is: ， wherein is the mutual inductance between the primary transmitting coil L P1 and the receiving coil L S , is the mutual inductance between the integrated counter transmitting coil L P2 and the receiving coil L S .
7. The dual-transmit compact underwater wireless power transmission system according to claim 5, wherein, Equivalent transmit inductance is: ， wherein is the mutual inductance between the main transmitting coil L P1 and the integrated counter transmitting coil L P2 and the integrated counter transmitting coil L 8. The dual-transmit compact underwater wireless power transmission system according to claim 7, wherein, According to the preset alternating current angular frequency, the corresponding circuit element parameter value is selected, and the preset alternating current angular frequency and the corresponding circuit element parameter value satisfy the following relationship: ， In the formula is a predetermined AC angular frequency.
Citation Information
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