Miniaturized broadband non-reflection filtering antenna and communication device

Abstract

The application provides a miniaturized broadband non-reflection filtering antenna and communication equipment, and relates to the field of communication antennas. The antenna comprises a hybrid coupling resonance system and a matching absorption network, wherein the hybrid coupling resonance system comprises a main radiation slot of an open loop structure provided on a metal ground plate, and two parasitic radiation slots of a U-shaped structure respectively located on both sides of the main radiation slot; the matching absorption network comprises an absorption resistor connected in parallel with a feeding microstrip line, and an absorption microstrip line connected in series with the absorption resistor. According to the application, the absorption circuit is integrated on the structure, so that the antenna presents the non-reflection characteristic in the range of 1.27-2.31 GHz which is far beyond the radiation bandwidth of the antenna, the defects of the traditional antenna, such as the in-band reflection and the out-of-band energy reflection back to the transmission channel to deteriorate the performance of the radio frequency front end, are effectively solved, and the electromagnetic compatibility performance and the linearity of the system as a whole are significantly improved.

Description

TECHNICAL FIELD

[0001] The present application relates to the field of communication antennas, in particular to a miniaturized wideband non-reflection filtering antenna and communication equipment. BACKGROUND

[0002] In the face of miniaturization and complex electromagnetic environment of wireless communication scenarios, non-reflection antennas, as a new technology, have great potential in solving the problems of traditional filtering antennas such as anti-interference and high reliability by integrating the "radiation-absorption" multi-functional characteristics. On the one hand, non-reflection antennas can achieve efficient radiation in the selected frequency passband, ensuring stable transmission of communication signals; on the other hand, non-reflection antennas can effectively realize the out-of-band matching of antennas and radio frequency front-end circuits by absorbing out-of-band interference signals, avoiding problems such as performance degradation and sensitivity reduction of the back-end active devices. Currently, non-reflection antennas generally use frequency complementary duplexing methods, but the design complexity of the non-reflection antennas is high.

[0003] For example, Chinese patent document CN116613533A (application number 2023107367792) discloses an embedded non-reflection microwave antenna, which realizes non-reflection effect without increasing the size by adding a defect microstrip structure in the slot of the patch, but the radiation bandwidth is narrow and the application range is narrow. For another example, Chinese patent document CN120262003A (application number 2025105723679) discloses a wideband non-reflection filtering antenna, which uses two microstrip band-stop filters, and the antenna structure is complex. In addition, the above-mentioned patents do not consider the application of slot antennas. SUMMARY

[0004] (I) Technical problems to be solved

[0005] In view of the deficiencies of the prior art, the present application provides a miniaturized wideband non-reflection filtering antenna and communication equipment, which solves the technical problem of how to provide a miniaturized wideband non-reflection filtering antenna with simple structure and high performance.

[0006] (II) Technical solutions

[0007] To achieve the above purpose, the present application is realized by the following technical solutions:

[0008] A miniaturized wideband non-reflection filtering antenna, comprising a dielectric substrate and a metal ground plate stacked in order from top to bottom, and a coaxial device;

[0009] A feed microstrip line is provided on the dielectric substrate, and a hybrid coupling resonance system is provided in the metal ground plate.

[0010] In the length direction of the feed microstrip line, the terminal of the feed microstrip line is connected to the metal ground plate through a first metal via hole.

[0011] In the width direction of the feeding microstrip line, the feeding microstrip line is connected in parallel with an absorbing microstrip line through an absorbing resistor, and a terminal of the absorbing microstrip line is connected to the metal ground plate through a second metal via hole; wherein the length of the absorbing microstrip line is one quarter of the wavelength at the working frequency of the antenna.

[0012] The inner conductor of the coaxial connector is connected to the feeding microstrip line, and the outer conductor is connected to the metal ground plate.

[0013] Preferably, the hybrid coupled resonant system comprises a main radiation slot which is coupled to the feeding microstrip line through a slot, and at least one parasitic radiation slot which forms secondary radiation with the coupled electromagnetic field.

[0014] Preferably, the parasitic radiation slot comprises a first parasitic radiation slot and a second parasitic radiation slot, and the first parasitic radiation slot and the second parasitic radiation slot are respectively located on both sides of the main radiation slot.

[0015] Preferably, the length of the main radiation slot is one half of the wavelength at the working frequency of the antenna.

[0016] Preferably, the main radiation slot as a whole presents an open loop structure.

[0017] Preferably, the length of the first parasitic radiation slot and the length of the second parasitic radiation slot are both one half of the wavelength at the frequency of the radiation zero point.

[0018] Preferably, the first parasitic radiation slot and the second parasitic radiation slot as a whole both present a U-shaped structure.

[0019] Preferably, the feeding microstrip line and the absorbing microstrip line are processed by etching.

[0020] Preferably, the material of the metal ground plate, the feeding microstrip line and the absorbing microstrip line is copper, and the material of the dielectric substrate is Rogers RO3003.

[0021] A communication device comprises the miniaturized wideband non-reflection filtering antenna as described above.

[0022] (Three) beneficial effects

[0023] The application provides a miniaturized wideband non-reflection filtering antenna and a communication device. Compared with the prior art, the application has the following beneficial effects:

[0024] The application is provided with a feeding microstrip line and an absorbing microstrip line in parallel through an absorbing resistor on one side of the feeding structure. The length of the absorbing microstrip line is one quarter of the wavelength of the working frequency of the antenna, and the terminal is connected with the metal floor through a metal via hole to realize the grounding short circuit. The one quarter of the absorbing microstrip line has the impedance transformation function. When the antenna works at the resonant frequency, the impedance of the input port of the absorbing microstrip line tends to infinity, equivalent to the open circuit state, and the absorbing resistor in series will not affect the radiation function. When the antenna works away from the resonant frequency, the absorbing resistor plays a role, and the out-of-band wave absorbing capacity of the system is significantly improved. It can be seen that the short-circuit quarter-wave transmission line with resistance loading as an absorbing unit can realize the single-frequency independent regulation and control of the radiation and absorption functions. At the same time, since the transmission length of the absorbing microstrip line is only one quarter of the wavelength, the antenna size will not be significantly increased, and the miniaturized design of the absorbing function is realized. BRIEF DESCRIPTION OF DRAWINGS

[0025] In order to more clearly illustrate the technical solutions in the embodiments of the present application or the prior art, the following will briefly introduce the drawings needed to be used in the embodiments or the prior art description. Obviously, the drawings in the following description are only some embodiments of the present application, and other drawings can also be obtained by those skilled in the art without creative labor.

[0026] Figure 1 The overall schematic diagram of a miniaturized wideband non-reflective filtering antenna is provided for the embodiments of the present application.

[0027] Figure 2 The front view of a miniaturized wideband non-reflective filtering antenna is provided for the embodiments of the present application.

[0028] Figure 3 The top view of a miniaturized wideband non-reflective filtering antenna is provided for the embodiments of the present application.

[0029] Figure 4 The front view of a matching absorbing network is provided for the embodiments of the present application.

[0030] Figure 5 The impedance and gain curve diagram of a miniaturized wideband non-reflective filtering antenna is provided for the embodiments of the present application.

[0031] Figure 6 The radiation efficiency curve diagram of a miniaturized wideband non-reflective filtering antenna is provided for the embodiments of the present application.

[0032] Figure 7 The directional diagram of a miniaturized wideband non-reflective filtering antenna in the XOZ plane is provided for the embodiments of the present application.

[0033] Figure 8The embodiment of the present application provides a miniaturized wideband non-reflection filtering antenna in the direction diagram of the YOZ plane.

[0034] Mark explanation:

[0035] 1-medium substrate, 2-main radiation slot, 3-first parasitic radiation slot, 4-second parasitic radiation slot, 5-feeding microstrip line, 6-absorbing microstrip line, 7-absorbing resistor, 8-coaxial device, 9-first metal via, 10-second metal via, 11-metal floor;

[0036] X-length direction of the feeding microstrip line, Y-width direction of the feeding microstrip line, Z-thickness direction of the antenna. Specific implementation

[0037] In order to make the purpose, technical scheme and advantages of the embodiment of the present application more clear, the technical scheme in the embodiment of the present application is clearly and completely described, obviously, the described embodiment is a part of the embodiment of the present application, rather than all the embodiments. Based on the embodiment in the present application, all other embodiments obtained by those skilled in the art without creative labor belong to the protection scope of the present application.

[0038] In order to better understand the above technical scheme, the above technical scheme will be described in detail in combination with the drawings of the specification and the specific implementation.

[0039] Embodiment 1:

[0040] As shown in the drawings, Figures 1-4 The embodiment of the present application discloses a miniaturized wideband non-reflection filtering antenna, which comprises a medium substrate 1 and a metal floor 11 stacked in turn from top to bottom, a feeding microstrip line 5, an absorbing microstrip line 6 and an absorbing resistor 7 arranged on the upper surface of the medium substrate 1, a hybrid coupling resonance system arranged on the metal floor 11, and a coaxial device 8.

[0041] Specifically,

[0042] Exemplarily, the feeding microstrip line 5 and the absorbing microstrip line 6 can be obtained by etching and processing on the upper surface of the medium substrate 1.

[0043] As shown in the drawings, Figure 1 and Figure 3 In the length direction of the feeding microstrip line 5, the terminal of the feeding microstrip line 5 is connected with the metal floor 11 through the first metal via 9, so as to realize grounding.

[0044] As shown in the drawings, Figure 1 , Figure 3 and Figure 4 In the width direction of the feeding microstrip line 5, the feeding microstrip line 5 is connected with the absorbing microstrip line 6 in parallel through the absorbing resistor 7. More specifically,Figure 4 The connection relationship between the components of the matching absorption network is that the feeding microstrip line 5 is connected in parallel with the absorption resistor 7, the absorption resistor 7 is connected in series with the input end of the absorption microstrip line 6, and the terminal of the absorption microstrip line 6 is grounded. In addition, the terminal of the absorption microstrip line 6 is connected with the metal ground plate 11 through the second metal via hole 10 to realize the ground short circuit. In particular, the length of the absorption microstrip line is designed as one quarter of the wavelength of the working frequency of the antenna, so that the absorption microstrip line has the impedance transformation function.

[0045] As shown in Figure 2 , the inner conductor of the coaxial device 8 is connected with the feeding microstrip line 5, and the outer conductor is connected with the metal ground plate 11.

[0046] The embodiment of the present application uses a resistance-loaded short-circuit quarter-wavelength transmission line as an absorption unit, which can realize independent regulation and control of the single-frequency point of radiation and absorption functions. At the same time, since the transmission length of the absorption microstrip line is only one quarter of the wavelength, the antenna size will not be significantly increased, and the miniaturization design of the absorption function is realized.

[0047] In an optional embodiment, as shown in Figure 1 and Figure 3 , the hybrid coupling resonance system includes a main radiation slot 2 (main resonator) which forms a slot coupling with the feeding microstrip line 5 and at least one parasitic radiation slot (parasitic resonator) which forms a secondary radiation with the coupled electromagnetic field.

[0048] As shown in Figure 1 and Figure 3 , the parasitic radiation slot includes a first parasitic radiation slot 3 and a second parasitic radiation slot 4, and the first parasitic radiation slot 3 and the second parasitic radiation slot 4 are respectively located on both sides of the main radiation slot 2.

[0049] As shown in Figure 1 and Figure 3 , the length of the main radiation slot 2 is one half of the wavelength of the working frequency of the antenna, and the whole presents an open loop structure. It should be noted that the open loop structure effectively reduces the size of the antenna, which is beneficial to miniaturization design.

[0050] As shown in Figure 1 and Figure 3 , the length of the first parasitic radiation slot 3 and the second parasitic radiation slot 4 is one half of the wavelength of the frequency at the radiation zero point, and the whole presents a U-shaped structure. It should be noted that the U-shaped structure is beneficial to impedance matching, and the opening direction of the U-shaped structure does not need to be specially limited.

[0051] The embodiment of the present application is based on the near-field parasitic coupling technology, and by loading a near-field parasitic unit structure (designing two U-shaped parasitic radiation slots), a corresponding out-of-band radiation zero point is introduced to improve the out-of-band selectivity and filtering performance.

[0052] In one alternative embodiment, the dielectric substrate 1 is made of Rogers RO3003 or other high-frequency circuit dielectric substrates; the metal ground plane 11, the feed microstrip line 5, and the absorber microstrip line 6 are made of copper or other metal materials.

[0053] To help understand the embodiments of the present invention, a specific example is provided below:

[0054] like Figure 3 As shown, the dielectric substrate 1 has a length of l1 = 60 mm and a width of w1 = 40 mm; the feed microstrip line 5 has a length of l8 = 34 mm and a width of w1 = 40 mm. 10 =1mm; the length of the absorbing microstrip line 6 is l7=24.5mm and the width is w9=7mm; the length of the main radiating slot 3 corresponds to 0.5 wavelengths of the antenna operating frequency; the lengths of the first parasitic radiating slot 4 and the second parasitic radiating slot 5 are 0.5 wavelengths of the frequency at their respective radiation null points; the resistance of the absorbing resistor 7 is R=100ohm.

[0055] like Figure 4 As shown, the absorbing microstrip line 6 and the absorbing resistor 7, which are connected in parallel to the right side of the feed microstrip line 5, are offset from the starting segment of the feed microstrip line by a distance of l. 10 =11mm.

[0056] The miniaturized broadband non-reflective filter antenna in the above example was simulated and analyzed using the 3D electromagnetic (EM) simulation software HFSS21.0. The resulting parameters and dimensions of the antenna are shown in Table 1 below.

[0057] Table 1 Optimal Dimensions for Each Parameter

[0058]

[0059] Based on the above parameters, HFSS was used to analyze the S11 parameters, gain, and radiation efficiency parameters of the miniaturized broadband non-reflective filter antenna in the above embodiment. The analysis results are as follows:

[0060] like Figure 5 As shown, the -10dB impedance curve of this example non-reflective antenna has a bandwidth of 1.04 GHz, from 1.27 GHz to 2.31 GHz, with a relative bandwidth of 58.1%; the peak gain is 4.81 dBi, and the gain suppression is 9.42 dBi.

[0061] like Figure 6 As shown, the peak radiation efficiency of the non-reflective antenna in this example is 98.27%.

[0062] like Figure 7As shown, the example of the reflectorless antenna has the characteristics of high gain co-polarization and cross-polarization suppression in the XOZ plane direction pattern at 1.734GHz.

[0063] As shown, the example of the reflectorless antenna has the characteristics of high gain co-polarization and cross-polarization suppression in the YOZ plane direction pattern at 1.734GHz. Figure 8

[0064] Embodiment 2:

[0065] The embodiment of the application discloses a communication device, comprising the miniaturized wideband reflectorless filtering antenna of embodiment 1.

[0066] Compared with the prior art, the application has the following beneficial effects:

[0067] 1. The embodiment of the application adopts a resistance-loaded short-circuit quarter-wavelength transmission line as an absorption unit, so that the radiation and absorption functions can be independently regulated and controlled at a single frequency point.

[0068] 2. The embodiment of the application is based on the near-field parasitic coupling technology, and a near-field parasitic unit structure (two U-shaped parasitic radiation slots) is loaded to introduce corresponding out-of-band radiation zeros, so as to improve the out-of-band selectivity and filtering performance.

[0069] 3. The embodiment of the application integrates the absorption circuit on the structure, so that the antenna has the reflectorless characteristic in the range of 1.27-2.31GHz far beyond the radiation bandwidth, effectively solves the defects of the in-band reflection of the traditional antenna and the energy reflection back to the transmission channel, and significantly improves the electromagnetic compatibility performance and the linearity of the system as a whole.

[0070] It should be noted that, in this document, the relationship terms such as first and second are only used to distinguish one entity or operation from another entity or operation, and do not necessarily require or imply any such actual relationship or order between the entities or operations. Moreover, the terms "include", "contain" or any other variants thereof are intended to cover non-exclusive inclusion, so that the process, method, article or device including a series of elements not only includes those elements, but also includes other elements not explicitly listed or inherent to such process, method, article or device. Without more limitations, the element defined by the statement "including a" does not exclude the presence of another identical element in the process, method, article or device including the element.

[0071] ​The above examples are only used to illustrate the technical solutions of the present application, and are not intended to limit the present application; although the present application has been described in detail with reference to the foregoing examples, those skilled in the art should understand that the technical solutions recorded in the foregoing examples can be modified, or some technical features can be replaced by equivalent features; and these modifications or replacements do not cause the essence of the corresponding technical solutions to deviate from the spirit and scope of the technical solutions of the embodiments of the present application.

Claims

1. A miniaturized broadband non-reflective filter antenna, characterized in that, It includes a dielectric substrate (1) and a metal ground plane (11) stacked from top to bottom, and a coaxial cable (8). The dielectric substrate (1) is provided with a feed microstrip line (5), and the metal ground plane (11) is provided with a hybrid coupling resonant system; The hybrid coupled resonant system includes a main radiation slot (2) that forms a slot coupling with the feed microstrip line (5) and a parasitic radiation slot that forms secondary radiation with the coupled electromagnetic field; the parasitic radiation slot includes a first parasitic radiation slot (3) and a second parasitic radiation slot (4), the first parasitic radiation slot (3) and the second parasitic radiation slot (4) being located on both sides of the main radiation slot (2). Along the length of the feed microstrip line (5), the input end of the feed microstrip line (5) is far from the hybrid coupled resonant system. The feed microstrip line (5) crosses the second parasitic radiation slot (4) from its input end and extends above the main radiation slot (2). The end of the feed microstrip line (5) is connected to the metal ground plane (11) through the first metal via (9). In the width direction of the feed microstrip line (5), the side of the feed microstrip line (5) away from the second parasitic radiation slot (4) is connected in parallel with the absorption resistor (7), the absorption resistor (7) is connected in series with the input terminal of the absorption microstrip line (6), and the terminal of the absorption microstrip line (6) is connected to the metal ground plane (11) through the second metal via (10); wherein the length of the absorption microstrip line (6) is one-quarter wavelength of the antenna operating frequency; The inner conductor of the coaxial cable (8) is connected to the input end of the feed microstrip line (5), and the outer conductor is connected to the metal ground plane (11). The axis of symmetry of the main radiation slot (2) is offset along the width direction of the feed microstrip line (5), and the offset direction points to the connection end of the feed microstrip line (5) and the absorption resistor (7). The axis of symmetry of the second parasitic radiation slot (4) is offset along the width direction of the feed microstrip line (5), and the offset direction is away from the connection end.

2. The miniaturized broadband reflection-free filter antenna as described in claim 1, characterized in that, The length of the main radiating slot (2) is half the wavelength of the antenna operating frequency.

3. The miniaturized broadband non-reflective filter antenna as described in claim 2, characterized in that, The main radiation groove (2) is generally presented as an open ring structure.

4. The miniaturized broadband non-reflective filter antenna as described in claim 1, characterized in that, The lengths of the first parasitic radiation trough (3) and the second parasitic radiation trough (4) are both half the wavelength of the frequency at the zero point of radiation.

5. The miniaturized broadband non-reflective filter antenna as described in claim 4, characterized in that, Both the first parasitic radiation trough (3) and the second parasitic radiation trough (4) are U-shaped structures.

6. The miniaturized broadband non-reflective filter antenna as described in claim 1, characterized in that, The feeding microstrip line (5) and the absorbing microstrip line (6) are processed by etching.

7. The miniaturized wideband reflection-free filter antenna as described in claim 1, characterized in that, The metal floor (11), the feed microstrip line (5) and the absorber microstrip line (6) are made of copper; the dielectric substrate (1) is made of Rogers RO3003.

8. A communication device, characterized in that, Includes the miniaturized broadband non-reflective filter antenna as described in any one of claims 1 to 7.

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