Compensated coupled transformer for across-inductor voltage regulator

Abstract

Various embodiments disclose a cross-inductor voltage regulator comprising a first switching circuit configuration pair, the first switching circuit configuration pair comprising a first set of switching circuits, a first compensating coupled inductor coupled to the first set of switching circuits, a second set of switching circuits, and a second compensating coupled inductor coupled to the second set of switching circuits, wherein the first compensating coupled inductor comprises a first winding of a compensating coupled transformer and the second compensating coupled inductor is a second winding of the compensating coupled transformer.

Description

[0001] background Fields of various embodiments The various embodiments generally relate to computer systems and circuits, and more specifically, to compensated coupling transformers for cross-inductor voltage regulators.

[0002] Description of related fields Computer devices and systems typically include various circuits for regulating the power delivered to different electronic components within these devices and systems during operation. For example, many computer devices include multiple power control circuits, such as voltage regulators, that control the power supplied by a power source by outputting a specific voltage to power one or more electrical components. High-performance computer devices and systems (such as servers, desktops, laptops, motherboards, and graphics processing units (GPUs)) often include power-consuming electronic components, thus requiring high, stable input power. To meet these requirements, designers may include voltage regulators in computer devices or systems to output high levels of power using high input current and high slew rates. One type of voltage regulator used for this purpose is a trans-inductor voltage regulator (TLVR), which is a switching circuit that provides high current and dynamic response during transitions, enabling the electronic components within the computer device or system to receive high, stable power from the power source. TLVRs also reduce the output capacitance required by the circuitry supplying input current to the electronic components, which in turn reduces the form factor of the capacitors in the circuitry and the overall footprint of the circuitry within the computer device or system.

[0003] Generally, a TLVR is a type of multiphase voltage regulator that includes multiple converters, each producing a target output voltage, wherein each converter includes a transformer. The secondary windings of the transformers in the respective converters are connected to form a circuit. Because the secondary windings are connected, a given converter controls the current flowing through the secondary windings of the other converters, even when the other converters do not actively sense current. Therefore, the output current generated by the circuit of the secondary windings rises or falls in all phases, enabling the TLVR to respond to load transients. In some cases, a TLVR may include additional windings and inductors to help control the amount of current ripple experienced during phase transitions.

[0004] One drawback of conventional TLVRs is the difficulty in modifying their topology. For example, designers can add compensating inductors to the secondary windings of the TLVR to adjust the inductance. However, including compensating inductors introduces current ripple into the TLVR, and including smaller compensating inductors results in larger output current ripple and lower output steady-state efficiency. Further attempts to improve TLVRs incorporating compensating inductors have led to even more problems. For instance, when modifying the TLVR and compensating inductors to improve transient response performance when transitioning to steady state, designers attempt to increase the coupling coefficient between the windings of the transformer included in the corresponding converter and reduce the self-inductance of the compensating inductor, which negatively impacts the steady-state efficiency of the TLVR. Conversely, when modifying the TLVR and compensating inductors to improve steady-state efficiency, designers attempt to reduce the coupling coefficient between the windings of the transformer included in the buck converter and increase the self-inductance of the compensating inductor, which negatively impacts the transient response performance of the TLVR.

[0005] As mentioned above, there is an urgent need in the art for more efficient designs of voltage regulators for use in computer equipment and systems. Summary of the Invention

[0006] Various embodiments disclose a trans-inductor voltage regulator comprising a first switching circuit pairing, the first switching circuit pairing including a first set of switching circuits, a first compensation coupling inductor coupled to the first set of switching circuits, a second set of switching circuits, and a second compensation coupling inductor coupled to the second set of switching circuits, wherein the first compensation coupling inductor includes a first winding of a compensation coupling transformer, and the second compensation coupling inductor is a second winding of the compensation coupling transformer.

[0007] Various embodiments also disclose a system including a first processor and a transinductor voltage regulator that generates a first voltage for the first processor.

[0008] At least one technical advantage of the disclosed multiphase TLVR design compared to existing technologies is that computer devices and systems can provide power to electronic components more efficiently and at a lower cost. For example, when operating in steady state, the compensated coupling transformer included in the disclosed design enables the multiphase TLVR to generate output power with lower losses and smaller current ripple than that achievable with conventional multiphase TLVRs. When operating under dynamic load conditions (such as boost or buck transitions), the compensated coupling transformer included in the disclosed design enables the multiphase TLVR to produce smaller transient outputs and recover in a shorter time, thereby reducing output capacitance compared to that experienced by conventional multiphase TLVRs. Furthermore, because the compensated coupling transformer included in the disclosed design occupies a smaller area on the circuit board than the two separate inductors included in conventional designs, the disclosed design allows a given printed circuit board to include a greater density of multiphase TLVRs than that achievable using conventional designs. Therefore, the disclosed design improves the overall ability to control power usage in high-performance computer devices and systems, as well as when performing high-performance applications. These technical advantages provide one or more technical improvements over prior art methods. Attached Figure Description

[0009] To gain a detailed understanding of the features described above in the various embodiments, reference can be made to the embodiments for a more specific description of the inventive concepts briefly summarized above, some of which are illustrated in the accompanying drawings. However, it should be noted that the drawings illustrate only typical embodiments of the inventive concept and should not be construed as limiting the scope in any way; other equally effective embodiments exist.

[0010] Figure 1A The diagram illustrates a circuit of a multiphase transinductor voltage regulator (TLVR) that can be used to power high-performance electronic components according to one or more aspects of this disclosure; Figure 1B The diagram illustrates a circuit of another multiphase transinductor voltage regulator (TLVR) that can be used to power high-performance electronic components according to one or more aspects of this disclosure; Figure 2 The illustration shows phase group pairing of phase converters included in a multiphase TLVR according to one or more aspects of the present disclosure, and the equivalent circuit of the phase group pairing; Figure 3 The illustrations depict one or more aspects of this disclosure. Figure 2 The waveforms of the individual components of the phase group pairing during the operation of one or more switching networks; Figure 4The illustration shows additional waveforms of the various components of the multiphase TLVR of FIG1 according to one or more aspects of the present disclosure during operation of one or more switching networks; Figure 5 The illustration depicts a boost operation according to one or more aspects of this disclosure. Figure 2 The waveforms of each component in the phase group pair; Figure 6 The illustration depicts a step-down operation according to one or more aspects of this disclosure. Figure 2 The waveforms of each component in the phase group pair; Figure 7 The illustration shows a compensation coupling transformer according to one or more aspects of this disclosure. Figure 2 The dynamic load performance curves of the phase group pairings compared to the phase group of the TLVR in Figure 1 without the compensation coupling transformer. Figure 8 A flowchart illustrating method steps for generating output power for electronic components according to one or more aspects of this disclosure is provided. Figure 9 The illustration depicts a computer system configured to implement one or more aspects of this disclosure. Detailed Implementation

[0011] In the following description, numerous specific details are set forth to provide a more thorough understanding of the various embodiments. However, it will be apparent to those skilled in the art that the inventive concepts can be practiced without one or more of these specific details.

[0012] Figure 1A The illustration shows a circuit diagram of a multiphase transinductor voltage regulator (TLVR) 100 that can be used to power high-performance electronic components according to one or more aspects of this disclosure. As shown, the TLVR 100 includes, but is not limited to, phase group 1 110, phase group 2 120, feedback network 160, and phase group pairing 170, which includes phase groups M 130. Phase Group N 140 and compensating coupling transformer 150. Each phase group includes two or more phase converters ( For example Phase 1 converter 112, Phase 2 converter 116, etc.). Each phase converter includes a switching network 102 ( For example Switching network 102 (1) etc.) and coupling transformer 104 ( For example Phase group 1 110 includes a compensating inductor 106, and phase group 2 120 includes a compensating inductor 108. The compensating coupling transformer 150 includes, but is not limited to, compensating coupling inductors 152 and 154.

[0013] The multiphase TLVR 100 is configured to receive input voltage V in And provide output voltage V to the load. out In the example illustrated in Figure 1, the load is represented as a resistive load R. load The resistive load R load Consume output current i o In some examples, the load is an electronic component incorporated into a computer device or system, such as a processor, memory, semiconductors, such as a central processing unit (CPU), graphics processing unit (GPU), high-current application-specific integrated circuit (ASIC), and / or field-programmable gate array (FPGA). As those skilled in the art will appreciate, a computing device or system including a load powered by a multiphase TLVR 100 can be any type of technically feasible computer system, including but not limited to server machines, server platforms, desktop machines, laptop machines, handheld / mobile devices, or wearable devices. Furthermore, those skilled in the art will understand that the multiphase TLVR 100 can also be used to power other types of components.

[0014] The multiphase TLVR 100 includes multiple phase groups ( For example (Phase groups include phase group 1 110, phase group 2 120, phase group M 130, phase group N 140, etc.), which include multiple phase converters. Each phase converter includes a switching network 102, which generates an output voltage V by driving an individual coupling transformer 104. out The phase. For example, a multiphase TLVR 100 includes a phase group 1 110, which includes phase 1 converter 112 to phase a converter 116. The switching network 102 (1) of phase 1 converter 112 generates a first-phase output current i corresponding to the output voltage of the first phase. 1-1 Similarly, the switching network of phase converter 116 generates the output current i. 1-a In the a-th phase, the switching network of the phase n converter 146 in group N 140 generates the phase current i. N-n And so on.

[0015] Each switching network 102 of the corresponding phase converter ( For example , 102(1) etc.) includes multiple switches and drivers. The drivers are based on control signals (such as pulse width modulation (PWM) control signals generated by feedback network 160) For example (PWM 1-1, etc.) controls the operation of each of the multiple switches. When the coupling transformer 104 is coupled to the input voltage V... inWhen the switch is turned on (or closed), the switch network 102 is coupled to the input voltage V. in Thus, the switching network 102 causes the coupled inductor 104 to generate a phase voltage V at the secondary winding of the phase converter. p When the switch is turned off (or open), the switch network 102 is connected to the input voltage V. in When the connection is broken, no phase voltage is generated at the secondary winding of the phase converter. When another switch is turned on, switch network 102 is coupled to ground, and when that other switch is turned off, switch network 102 is disconnected from ground. In the example illustrated in Figure 1, each switch network 102 includes two switches and one driver. However, in some embodiments, each switch network 102 includes a different number of switches and / or drivers.

[0016] As will be described in more detail herein, during operation, feedback network 160 generates one or more control signals for controlling the operation of switching network 102 based on measurements indicating the voltage and / or current flowing through multi-phase TLVR 100 and / or associated with the voltage and / or current flowing through multi-phase TLVR 100. For example, feedback network 160 may generate one or more PWM signals based on measurements indicating the current flowing through multi-phase TLVR 100 and / or associated with the current flowing through multi-phase TLVR 100. During operation, feedback network 160 will use one or more control signals ( For example PWM signals (1-1, 1-a, 2-1, etc.) are applied to a driver included in the switching network 102 to control the frequency and / or duty cycle of the switches included in the switching network 102 on and off. The feedback network 160 can be implemented as any suitable control device and / or circuit for controlling the operation of the switching network 102. For example, the feedback network 160 can be implemented as one or more of the following: analog control circuitry, digital control circuitry, microprocessor, integrated circuit, and / or any other suitable control device for controlling the operation of the switching network 102. As another example, the feedback network 160 can be implemented as a PWM controller that controls the PWM signals based on the output voltage and / or output current.

[0017] Each coupling transformer T 104 included in the phase converter includes a primary winding L p and secondary winding L s The primary winding of the coupling transformer T104 (e.g., L) p(1-1) (etc.) is coupled to the output of the corresponding switching network 102, such that the phase current i generated by the corresponding switching network 102 flows through the primary winding of the coupling transformer 104. For example, the coupling transformer T of the phase-1 converter 112 1-1 The primary winding L included in 104(1) p(1-1)The output coupled to the switching network 102(1) causes the first phase current i generated by the switching network 102(1) to... 1-1 Flow through coupling transformer T 1-1 104(1) primary winding L p(1-1) Similarly, the coupling transformer T of the a-th phase converter 116 1-a The primary winding L included p(1-a) The output of the switching network 102 coupled to the a-th phase makes the a-th phase current i generated by the switching network 102... 1-a The current flows through the a-th phase coupling transformer T 1-a 104 primary winding L p(1-a) And so on. Each coupling transformer 104 also includes a secondary winding L s As shown in Figure 1, the secondary windings L of multiple coupled transformers 104 in a given group s ( For example L s(M-1) To L s(M-n) ) are coupled in series with each other. For example, the secondary winding L of the coupling transformer 104(1) of the phase 1 converter 112. s(1-1) The secondary winding L of the coupling transformer 104 to the a-th phase converter 116 s(1-a) Series coupling. The mutual inductance M of each transformer represents the additional inductance in the circuit besides the self-inductance L of each inductor included in transformer T. For example, the coupling transformer T included in phase 1 converter 112. 1-1 104(1) Except for the self-inductance L of the first winding p(1-1) The self-inductance L of the second winding s(1-1) In addition, it also includes mutual induction M 1-1 In some embodiments, the mutual inductance M can be modeled as one or more separate inductors (not shown) coupled to the windings of a transformer.

[0018] In various embodiments, the multiphase TLVR 100 includes one or more phase groups ( For example Phase group 1 110 and phase group 2 120), the one or more phase groups include those with inductance L c And a compensation inductor series coupled to the secondary winding of the phase group ( For example (e.g., 106, 108, etc.). For example, the compensating inductor L c1 106 is coupled in series with the secondary winding of each transformer in phase group 1 110. Therefore, the current i flowing through the compensating inductor 106 c1The current flowing through the secondary winding of the coupling transformer 104 included in phase group 1 110 is the same. Alternatively, in some embodiments, the multiphase TLVR 100 includes only a compensating coupling inductor comprising a component as a compensating coupling inductor 150. For example The phase groups (152, 154).

[0019] In various embodiments, the phase compensation inductor is separate from the compensation inductor 108. Further, phase groups M 130 and N 140 include a single compensation coupling transformer 150. As a result, because the compensation coupling transformer 150 occupies a smaller area on the printed circuit board than the separate compensation inductors 106, 108, the phase group pair 170 formed by phase groups M 130 and N 140 occupies a reduced area compared to phase groups 110, 120. Consequently, when compared to phase groups 110, 120, phase group pair 170 saves more PCB area, has higher power density, and reduces PCB cost.

[0020] In various embodiments, the multiphase TLVR 100 further includes one or more phase group pairs ( For example Phase group pairing between two phase groups (170). For example, phase group M 130 is coupled through a compensation coupling transformer T. c(M-N) Phase 150 is paired with phase group N140 to form phase group pair 170. In this case, each phase group in phase group pair 170 includes a compensating coupling inductor included in the compensating coupling transformer 150. For example (152, 154). The compensating coupling inductor has self-inductance L c And coupled in series to the secondary winding L of the coupling transformer 104 included in the phase group. s For example, the compensating coupling inductor L cM 152 is coupled in series to the secondary winding L included in phase group M 130. s(M-1) To L s(M-n) Similarly, the compensating coupling inductor L cN 154 is coupled to the secondary winding L included in phase group N 140. s(N-1) To L s(N-n) In various embodiments, the phase groups 130 and 140 included in phase group pairing 170 include the same number of phases. For example, phase group M 130 includes the same number of n phases as phase group N 140.

[0021] In various embodiments, the compensation coupling transformer 150 has a mutual inductance M based on the coupling between the compensation coupling inductors 152 and 154. c(M-N)156. In some embodiments, the compensating coupling inductor 152 is negatively coupled to the compensating coupling inductor 154. In such instances, the mutual inductance 156 of the compensating coupling transformer 150 is based on negative coupling. As will be discussed in further detail below, the negative coupling between the circuit formed by the compensating coupling inductor 152 and the secondary winding of phase group M 130 and the circuit formed by the compensating coupling inductor 154 and the secondary winding of phase group N 140 reduces the phase current ripple generated by the phase group pairing 170, while improving transient response performance during steady-state transitions.

[0022] Figure 1B The illustration shows a circuit diagram of another multiphase transinductor voltage regulator (TLVR) 180, which can be used to power high-performance electronic components according to one or more aspects of this disclosure. As shown, but not limited to, the TLVR 180 includes phase group 1 110, phase group 2 120, feedback network 160, and phase group pairing 182. Phase group pairing 180 includes phase group M130, phase group N 190, and compensation coupling transformer 186. Compensation coupling transformer 182 includes, but is not limited to, compensation coupling inductors 152 and 184.

[0023] Multiphase TLVR 180 is similar to multiphase TLVR 100. Because the secondary winding of coupling inductor 104 in phase converters 192 and 196 is negatively coupled to the primary winding of coupling inductor 104, the phase group N 190 of multiphase TLVR 180 differs from the phase group N 140 of multiphase TLVR 100. Furthermore, the compensation coupling transformer 150 of phase group pairing 182 includes compensation coupling inductor 184, which is positively coupled to compensation coupling inductor 152, thereby generating mutual inductance M based on the series connection of compensation coupling inductor 184 with the secondary winding of phase group N 190. c(M-N) 186. As will be discussed in further detail below, the coupling between the circuit formed by the compensating coupling inductor 152 and the secondary winding of phase group M 130 and the circuit formed by the compensating coupling inductor 184 and the secondary winding of phase group N 190 reduces the phase current ripple generated by phase group pairing 182, while improving transient response performance during steady-state transitions.

[0024] Figure 2 The illustration shows a phase pairing 202 of a phase converter included in a multiphase TLVR according to one or more aspects of this disclosure, and equivalent circuits 250, 260 of the phase pairing 202. As shown, Figure 2The diagram illustrates a phase pair 202 of a multiphase TLVR circuit operating in steady state, a circuit 250 including a portion of the equivalent inductance of the phase pair 202, and a circuit 260 including the equivalent inductance of the decoupled phase pair 202 based on the compensating coupling inductors 218 and 238 included in the compensating coupling transformer 220. The phase pair 202 includes, but is not limited to, phase pair X 204 and phase pair Y 206. Phase pair X 204 includes, but is not limited to, circuit 210. Phase pair Y 206 includes, but is not limited to, circuit 230.

[0025] During operation, the equivalent inductance of the corresponding series 210, 230 of the inductors formed by the secondary side of the coupling transformer 104 and the compensating coupling inductors 218, 238 included in the compensating coupling transformer 220 is greater than the equivalent inductance achieved when the compensating inductors are not coupled to each other in steady state. As a result, using the phase pairing 202 of the compensating coupling transformer 220 reduces the current ripple of the output voltage and improves the efficiency of generating the output voltage.

[0026] The phase group pairing 202 of the multiphase TLVR includes a first series connection 210, which includes the series connection of the secondary windings of the coupling transformer 104 included in phase group X 204. The first series connection 210 is coupled to a first compensated coupling inductor 218. The phase group pairing 202 of the multiphase TLVR also includes a second series connection 230 of the secondary windings of the coupling transformer 104 included in phase group Y 206, coupled to a second compensated coupling inductor 238. Compensated coupling inductor L cX 218, L cY 238 is the compensation coupling transformer T cXY The winding is 220. As shown, the compensating coupling inductors 218 and 238 are negatively coupled to each other and have mutual inductance M. cXY 240.

[0027] In various embodiments, circuit 250 represents the equivalent circuit of the circuit formed by the first series 210, the second series 230, and the compensating coupling transformer 220. For example, when the coupling transformers 104 of each phase converter have the same parameters ( example likeWhen the self-inductance L, coupling coefficient k, turns ratio 1:1, etc. are the same, a transformer model can be used to replace the coupled inductor model, and the secondary windings can be combined and represented by equivalent inductors. For example, the coupled inductors in series 210, 230 and / or the compensating coupled inductors 218, 238 in the compensating coupled transformer 220 can have substantially similar inductances in the range of 350-450nH and substantially similar coupling coefficients in the range of 0.4-0.6. Circuit 250 includes a first series connection including a first equivalent inductor 252 having an inductance equivalent to that of the series connection of inductors 212, 214, 216 included in the first series connection 210. Circuit 250 includes a second series coupled to the first series, wherein the second series includes a second equivalent inductor 254 having an inductance equivalent to that of the series inductors 232, 234, 236 included in the second series 230.

[0028] For circuit 250, the voltage across each series circuit can be calculated based on the inductance of the equivalent inductors 252 and 254, the self-inductance of the compensating coupling inductors 218 and 238, and the mutual inductance 240 of the compensating coupling transformer 220. Equation 1 Equation 2 When the mutual inductance 240 of the compensating coupling transformer 220 is taken into account, circuit 260 represents the equivalent circuit of circuit 250. In this type of example, the compensating coupling inductors 218, 238 of the compensating coupling transformer 220 are decoupled, and the mutual inductance 240 is represented by a separate inductor (not shown) in each series connection. Circuit 260 includes a circuit with an inductance L equivalent to the first equivalent inductor 252. cX_eq The circuit includes a third equivalent inductor 262, a compensating coupling inductor 218, and an inductor representing the mutual inductance 240 of the compensating coupling transformer 220. Circuit 260 also includes an inductor with inductance L equivalent to the second equivalent inductor 254. cY_eq The fourth equivalent inductor 264, the compensation coupling inductor 238, and the inductor representing the mutual inductance 240 of the compensation coupling transformer 220.

[0029] As shown, the coupling coefficient k associated with the first equivalent inductor 252 and the second equivalent inductor 254 is... e It is based on the first equivalent inductor, the second equivalent inductor, and the compensating coupling inductors 218 and 238. For example, when the compensating coupling inductors 218 and 238 are equivalent to ( For example The same sense of self L c Mutual induction is M cAnd when the turns ratio is 1:1, the coupling coefficient is: Equation 4 Similarly, the coupling coefficient k of the compensation coupling transformer 220 c It is based on the mutual inductance 240 of the compensating coupling transformer 220 and the self-inductance of the compensating coupling inductors 218 and 238: Equation 4 Based on the voltage derived in Equations 1-2 and the coupling coefficient derived in Equations 3-4, the equivalent inductance of each series circuit in equivalent circuits 250 and 260 can be derived as a function of voltage: Equation 5 Equation 6 For example, regarding Figure 3-4 As further discussed, the inductance of the third equivalent inductor 262 and / or the fourth equivalent inductor 264 can be determined for each steady-state phase.

[0030] Figure 3 The illustrations depict one or more aspects of this disclosure. Figure 2 The phase group pair 202 represents the waveform 300 of each component during the operation of one or more switching networks. As shown, Figure 3 The diagram illustrates waveform 300, which comprises pulse width modulated pulses of phases M-1 to M-3 over one or more time periods, with a delay of 320 between each pulse. PWM Y-1 322 generates pulses of phase Y-1, PWM Y-2 326 generates pulses of phase Y-2, and PWM Y-3 330 generates pulses of phase X-3. Similarly, waveform 300 comprises pulse width modulated pulses of phase X-1 to X-2, with a delay of 320 between each pulse. In various embodiments, the delay 318 between the Y pulse and X is equal to half the delay 320 between PWM pulses in the same group. Waveform 300 also includes equivalent voltages and currents of circuit 250, which include a voltage V along the first series connection. cX 344 and current i cX 354, and the voltage V along the second series connection. cY 342 and current i cY 352.

[0031] During operation, phase pair 202 enters a steady state at different times based on a control signal. In various embodiments, feedback network 160 generates PWM pulses 322-332 to control switches included in the corresponding switching network 102. For example, a driver included in the phase pair 202 receives PWM pulse 322 and causes the phase pair 202 to operate in a first steady state during time periods between t1 302 and t2 304, t3 306 and t4 308, and t5 310 and t6 312, where only the PWM pulse is high and all other PWM pulses 324-332 are low. Alternatively, in some embodiments, the duty cycle of the PWM pulses 322-332 is longer. In such instances, two or more PWM pulses 322-332 overlap and operate in different steady states. In other examples, all PWM pulses are low. For example, phase pair 202 can operate in a second steady state during the time periods between t2 304 and t3 306, t4 308 and t5 310, and t6 312 and t7 314. During these time periods, all PWM pulses 322-332 are low.

[0032] When operating in the first steady state, the voltage across each series terminal in circuits 250 and 260 can be derived from the input and output voltages. For example, for phase group X 204 and phase group Y 206 in phase group pair 202, each phase group includes 3 PWMs, and 1 PWM drives m phases, thus generating a total of n phases. In this example, 1 PWM pulse drives the switching network 102 in the Y phase group ( For example PWM pulse 322 during the time period between t1 302 and t2 304; PWM pulse 326 during the time period between t5 310 and t6 312. In this type of example, the voltage along each series connection in circuit 250 during each time period is as follows: Equation 7 Equation 8 Based on these calculated voltages, the equivalent inductance of circuit 260 can be derived for the first steady state: Equation 9 Equation 10 in D This refers to the duty cycle of phase group pair 202. In some embodiments, one PWM pulse drives... Y Switching network 102 in phase group ( For example , t 3 306 and t 4PWM pulses 324 during the time period between 308. In this type of example, the voltage along each series connection of the equivalent circuit 250 and the equivalent inductances 262, 264 of the circuit 260 are reversed: Equation 11 Equation 12 Equation 13 Equation 14 When operating in the second steady state, all PWM pulses 322-332 are low, and the voltage across each series connection in circuit 250 can be derived from the output voltage. For example, for phase group X 204 and phase group Y 206 in phase group pair 202, each phase group includes 3 PWMs, and 1 PWM drives m phases, resulting in a total of n phases. In this type of example, the voltage along each series connection in circuit 250 during this period is as follows: Equation 15 In such instances, the inductance of the equivalent inductors 262 and 264 of the second steady-state derivation circuit 260 can be considered, wherein the equivalent inductance of each series connection is equal and based on the compensated coupling inductors 218 and 238: Equation 16 Figure 4 The diagram illustrates additional waveforms 400 of the various components of the multiphase TLVR of Figure 1 according to one or more aspects of this disclosure during operation of one or more switching networks. As shown, waveform 400 includes pulse width modulation pulses 322-326, 422, 424. Waveform 400 also includes a current i along the first series connection. cX 354. The current i along the second series connection cY 352, and the current in the first winding of each phase converter included in phase group X 204 and phase group Y 206. The current in the first winding includes the current i in the first winding of the coupling transformer 104 in the Y-1 switching circuit. Y-1 356. The current i in the first winding of the coupling transformer 104 in the X-1 switching circuit. X-1 452. The current i in the first winding of the coupling transformer 104 in the Y-2 switching circuit. Y-2 454, and the current i in the first winding of the coupling transformer 104 in the X-2 switching circuit. X-2 456.

[0033] As shown, the current in the first winding of each phase converter follows a similar pattern, wherein the current in the first winding peaks in response to pulses provided by switching network 102 and gradually decreases with the current ripple caused by pulses provided by other switching networks 102 in the phase converters of the phase group pairing 202. The current i in the first series 210 of circuit 250... cX 354 is based on the operation of the switching network 102 in the X group and at least on the currents 452, 456 flowing through the first winding of the coupling transformer 104 in the phase group X 204. Further, due to the mutual inductance associated with the compensating coupling transformer 220, the current i cX 354 is also partly based on the current i flowing through the secondary winding and the series 230 of the compensating coupling inductor 238. cY 352. Similarly, the current i in the second series circuit 230 in circuit 250 is... cY 352 is based on the operation of the switching circuit in phase group Y 206 and at least on the currents 356 and 454 flowing through the first winding of the coupling transformer 104 in phase group Y 206. Further, due to the mutual inductance 240 associated with the compensating coupling transformer 220, the current i cY 352 is also based in part on the series current i flowing through inductors 212, 214, 216 and the compensating coupling inductor 218. cX 354.

[0034] As shown, when phase pair 202 operates in steady state, phase currents 354, 452, 454, 456 are based at least on the additional mutual inductance 240 associated with the compensation coupling transformer 220. Consequently, this is in contrast to coupling inductors that do not have mutual inductance (…). example like Compared to the phase currents of the phase groups of the compensating inductors 106 and 108, the phase currents 354, 452, 454, and 456 are smaller and have lower peak-to-peak values. Therefore, the phase group pair 202 reduces the risk of inductor saturation by using inductors that operate with lower saturation currents, alleviates heat dissipation stress, and allows for the use of smaller heat sinks, thereby reducing product costs and improving reliability.

[0035] Figure 5 The illustration depicts a boost operation according to one or more aspects of this disclosure. Figure 2 The phase group pair 202 consists of waveforms for each component. As shown, waveform 500 includes PWM pulses 322-332 along the first series 210 and voltage V. cX 344 and current i cX 354, and the voltage V along the second series 230 cY 342 and current icY 352, the load current i provided by phase group pairing 202 load 522 and output voltage V out 524.

[0036] Phase pair 202 initially operates in steady state 502, then transitions to a first dynamic load (load boost) state 504 and a recovery state 506 before returning to steady state 508. When operating in the first dynamic load state 504, the load is boosted while all PWM pulses 322-332 are almost high. In this type of example, the inductance of the equivalent inductors 262, 264 of circuit 260 can also be derived as the inductance of circuit 260 operating in the second steady state, as shown in Equation 16 above. Since the inductance of the equivalent inductors 262, 264 operating in dynamic load state 504 is similar to the inductance of the equivalent inductors 262, 264 operating in the second steady state, the use of phase pair 202 of the compensated coupling transformer 220 reduces the fluctuation of the output voltage 524, thereby improving the efficiency of generating the output voltage 524 and reducing the output capacitance.

[0037] Figure 6 The illustration depicts a step-down operation according to one or more aspects of this disclosure. Figure 2 The phase group pair 202 consists of waveforms 600 for each component. As shown, waveform 500 includes voltage along the first series PWM pulses 322-332. V cX 344 and current i cX 354, and the voltage along the second series connection. V cY 342 and current i cY 352, the load voltage provided by phase group pairing 202 i load 522 and output voltage V out 524.

[0038] Phase pair 202 initially operates in steady state 508, then transitions to a second dynamic load state (load boost) 604 and a recovery state 606 before returning to steady state 608. Phase pair 202 operates in the second dynamic load state, where the load is bucked when almost all PWM pulses 322-332 are low. In this type of instance, the inductance of the equivalent inductors 262, 264 is also equal to the equivalent value of the inductance when operating in the second steady state, as shown in Equation 16 above. Since the equivalent inductance when operating in the dynamic load state is similar to the equivalent inductance in the second steady state, the use of compensated coupling transformer 220 in phase pair 202 reduces the fluctuation of output voltage 524, thereby improving the efficiency of generating output voltage 524 and reducing output capacitance.

[0039] Figure 7 The illustration shows a compensation coupling transformer 220 according to one or more aspects of this disclosure. Figure 2 The dynamic load performance of phase group pair 202 is shown in graph 700 compared to phase groups 110 and 120 of the TLVR 100 of Figure 1 excluding the compensation coupling transformer. As shown, graph 700 includes graph 710, which compares the buck response 704 of phase group 1110 and phase group 2 120 with the buck response 702 of phase group pair 202. Graph 700 also includes graph 720, which compares the boost response 724 of phase group 1 110 and phase group 2 120 with the boost response 722 of phase group pair 202.

[0040] As shown in Figure 700, the phase group pairing including phase groups 130 and 140 exhibits better transient performance compared to phase group 110 during both load boost and load buck cycles. For example, phase group 110 generates an output voltage with a peak-to-peak value of 215.2 mV. In contrast, the phase group pairing including phase groups 130 and 140 generates an output voltage with a peak-to-peak value of 196.4 mV.

[0041] Figure 8 A flowchart illustrating method steps for generating output power of an electronic component according to one or more aspects of this disclosure is provided. Steps for sensing current in a multiphase TLVR are also included, according to various embodiments. Although the method steps have been described in conjunction with the system of Figures 1-7, those skilled in the art will understand that any system configured to perform the method steps in any order falls within the scope of this disclosure.

[0042] As shown, method 800 begins at step 802, where TLVR 100 drives phase group pair 170 to operate in a first steady state. In various embodiments, the switching network 102 included in at least one of the phase converters 132, 136, 142, 146 drives the corresponding phase converter 132, 136, 142, 146 to operate in the first steady state. For example, the switching network of the phase 1 converter 132 included in phase group M130 drives the coupling transformer 104 of the phase 1 converter 132. The secondary winding of the coupling transformer 104 is included in series with the secondary winding of the coupling transformer 104 included in phase group M130. Based on the operation of the secondary winding in the phase 1 converter 132, the phase group pair 170 of phase group M130 and phase group N140 operates in the first steady state. When operating in the first steady state, the secondary winding of the coupling transformer 104 ( For example The voltage across the circuit of the secondary winding (included in phase group M 130) and the compensation coupling inductor 152 is based on the output voltage generated by TLVR 100 and / or the input voltage received by TLVR 100.

[0043] At step 804, TLVR 100 transitions to a dynamic load off state. In various embodiments, the switching network causes the phase pairings to operate in a first dynamic load state 504 and a recovery state 506 before returning to steady state 508. When operating in the first dynamic load state 504, the load is boosted while all PWM pulses 322-332 are almost high. In this type of example, the secondary winding of coupling transformer 104 ( For example The inductance of the circuit including the secondary winding in phase group M 130 and the compensation coupling inductor 152 is equal to the inductance of the same circuit when operating in the second steady state.

[0044] At step 806, the TLVR 100 drives phase group pair 170 to operate in the second steady state. When operating in the second steady state, all switching networks in phase group M 130 and phase group N 140 are low, and the voltage across the secondary winding of the coupling transformer 104 and the circuit of the compensating coupling inductor 152 is based on the output voltage of the TLVR 100.

[0045] At step 808, TLVR 100 transitions to an on-dynamic load state. In various embodiments, the switching network causes the phase pairings to operate in a second dynamic load state 604 and a recovery state 606 before returning to a steady state. Phase pairing 170 operates in the second dynamic load state 604, where the load is stepped down when almost all PWM pulses 322-332 are low. In this type of example, the inductance of the secondary winding of the coupling inductor and the circuitry of the compensating coupling inductor 152 is equal to the inductance of the circuitry when operating in the second steady state. In various embodiments, TLVR 100 can transition from an on-dynamic load state to first steady state operation.

[0046] Figure 9 The illustration depicts a computer system configured to implement one or more aspects of this disclosure. As shown, the computer system 900 includes, but is not limited to, a central processing unit (CPU) 902 and system memory 904 coupled to a parallel processing subsystem 912 via a memory bridge 905 and a communication path 913. The memory bridge 905 is also coupled to an I / O (input / output) bridge 907 via a communication path 906, and the I / O bridge 907 is in turn coupled to a bus 916.

[0047] In various embodiments, one or more components of the computer system 900 ( For example The CPU 902, parallel processing subsystem 912, etc., include one or more circuit boards that incorporate one or more TLVRs 100 as part of a circuit system. For example, the circuit board containing the CPU 902 may include one or more switching power circuits that include at least one TLVR 100.

[0048] In operation, I / O bridge 907 is configured to receive user input from input device 908 (such as a keyboard or mouse) and forward the input to CPU 902 for processing via communication path 906 and memory bridge 905. Bus 916 is configured to provide connectivity between I / O bridge 907 and other components of computer system 900 (such as network adapter 918 and various add-on cards 920 and 921).

[0049] As also shown, I / O bridge 907 is coupled to system disk 914, which can be configured to store content, applications, and data for use by CPU 902 and parallel processing subsystem 912. In general, system disk 914 provides non-volatile storage for applications and data and may include fixed or removable hard disk drives, flash memory devices, and CD-ROMs (optical disc read-only memory), DVD-ROMs (digital versatile discs), Blu-ray, HD-DVDs (high-definition DVDs), or other magnetic, optical, or solid-state storage devices. Finally, although not explicitly shown, other components such as universal serial bus or other port connections, optical disc drives, digital versatile disc drives, movie recording devices, etc., may also be connected to I / O bridge 907.

[0050] In various embodiments, memory bridge 905 may be a northbridge chip, and I / O bridge 907 may be a southbridge chip. Additionally, communication paths 906 and 913, as well as other communication paths within the computer system 900, may be implemented using any technically suitable protocol, including but not limited to AGP (Accelerated Graphics Port), HyperTransport, or any other bus or point-to-point communication protocol known in the art.

[0051] In some embodiments, the parallel processing subsystem 912 includes a graphics subsystem that delivers pixels to a display device 910, which can be any conventional cathode ray tube, liquid crystal display, light-emitting diode display, etc. In such embodiments, the parallel processing subsystem 912 incorporates circuitry optimized for graphics and video processing, including, for example, video output circuitry. (See below for further details.) Figure 2 As described in more detail herein, such circuitry can be incorporated across one or more parallel processing units (PPUs) included within the parallel processing subsystem 912. In other embodiments, the parallel processing subsystem 912 includes circuitry optimized for general-purpose and / or computational processing. Furthermore, such circuitry can be incorporated across one or more PPUs included within the parallel processing subsystem 912, which are configured to perform such general-purpose and / or computational operations. In yet another embodiment, one or more PPUs included within the parallel processing subsystem 912 may be configured to perform graphics processing, general-purpose processing, and / or computer processing operations. System memory 904 includes at least one device driver 903 configured to manage the processing operations of one or more PPUs within the parallel processing subsystem 912. System memory 904 also includes any number of software applications executing on CPU 902 and capable of issuing commands to control the operation of the PPUs.

[0052] In various embodiments, the parallel processing subsystem 912 may be integrated with one or more other elements of FIG. 1 to form a single system. For example, the parallel processing subsystem 912 may be integrated with the CPU 902 and other interconnect circuitry on a single chip to form a system-on-a-chip (SoC).

[0053] It should be understood that the systems shown herein are illustrative, and variations and modifications are possible. The connection topology, including the number and arrangement of bridges, the number of CPUs 902, and the number of parallel processing subsystems 912, can be modified as desired. For example, in some embodiments, system memory 904 may be connected directly to CPU 902 instead of via memory bridge 905, and other devices may communicate with system memory 904 via memory bridge 905 and CPU 902. In other alternative topologies, parallel processing subsystems 912 may be connected to I / O bridge 907 or directly to CPU 902, instead of via memory bridge 905. In yet another embodiment, I / O bridge 907 and memory bridge 905 may be integrated into a single chip, rather than existing as one or more discrete devices. Finally, in some embodiments, Figure 7 One or more of the components shown may be absent. For example, bus 916 may be eliminated, and network adapter 918 and add-on cards 920, 921 may be directly connected to I / O bridge 907.

[0054] In summary, a multiphase transinductor voltage regulator (TLVR) provides an output voltage to a load, such as electronic components included in a high-performance computing system or device. A multiphase TLVR comprises phase group pairs of phase converters that can generate high-power direct output current and voltage. Each phase group in the phase group pair includes multiple phase converters, each of which includes a switching network and a coupling transformer that generates output current at different times. The output side of each phase group is connected to a compensation coupling inductor, which adjusts the inductance associated with the secondary transformer included in the phase group. The compensation coupling inductor in the pair is the primary and secondary windings of the compensation coupling transformer. In some embodiments, the compensation coupling inductor is negatively coupled. The compensation coupling transformer includes two separate self-inductances and a mutual inductance associated with the coupling between the compensation coupling inductors.

[0055] Compared to existing technologies, at least one technical advantage of the disclosed multiphase TLVR design is that computer devices and systems can provide power to electronic components more efficiently and at a lower cost. For example, when operating in steady state, the inductors of the compensated coupling transformer included in the disclosed design enable the multiphase TLVR to generate output power with lower losses and smaller current ripple than that achievable with conventional multiphase TLVRs. When operating under dynamic load conditions (such as boost or buck transitions), the compensated coupling transformer included in the disclosed design enables the multiphase TLVR to produce smaller transient outputs and recover in a shorter time, thereby reducing output capacitance compared to conventional multiphase TLVRs. Furthermore, because the compensated coupling transformer included in the disclosed design occupies a smaller area on the circuit board than the two separate inductors included in conventional designs, the disclosed design allows a given printed circuit board to include a higher density of multiphase TLVRs than that achievable with conventional designs. Therefore, the disclosed design improves the overall ability to control power usage in high-performance computer devices and systems, as well as when executing high-performance applications. These technological advantages provide one or more technological improvements over existing technological approaches.

[0056] 1. In various embodiments, a transinductor voltage regulator includes a first pair of switching circuits, the first pair of switching circuits comprising: a first set of switching circuits; a first compensation coupling inductor coupled to the first set of switching circuits; a second set of switching circuits; and a second compensation coupling inductor coupled to the second set of switching circuits, wherein the first compensation coupling inductor includes a first winding of a compensation coupling transformer, and the second compensation coupling inductor is a second winding of the compensation coupling transformer.

[0057] 2. The trans-inductor voltage regulator as described in Clause 1, wherein the second compensated coupling inductor is negatively coupled to the first compensated coupling inductor.

[0058] 3. A trans-inductor voltage regulator as described in Clause 1 or 2, wherein the second compensated coupling inductor is positively coupled to the first compensated coupling inductor.

[0059] 4. The trans-inductor voltage regulator as described in any one of Clauses 1-3, wherein the first set of switching circuitry includes a multiphase converter, the multiphase converter comprising at least: a first converter for a first phase, the first converter including a first switching network and a first coupling transformer; and a second converter for a second phase, the second converter including a second switching network and a second coupling transformer.

[0060] 5. The trans-inductor voltage regulator as described in any one of Clauses 1-4, wherein the first coupling transformer includes a first primary coupling winding and a second primary coupling winding, the second coupling transformer includes a second primary coupling winding and a second primary coupling winding, and the first primary coupling winding and the second primary coupling winding are connected in series.

[0061] 6. The trans-inductor voltage regulator as described in any one of Clauses 1-5, wherein the first compensated coupling inductor is connected in series with the first primary winding and the second primary winding.

[0062] 7. The trans-inductor voltage regulator as described in any one of clauses 1-6 further includes a feedback network that, during operation, receives outputs from the first set of switching circuit pairs and generates a feedback signal that is transmitted to the first set of switching circuits and the second set of switching circuits.

[0063] 8. A trans-inductor voltage regulator as described in any one of Clauses 1-7, wherein the compensated coupling transformer has a self-inductance in the range of 350-450 nH and a coupling coefficient in the range of 0.4-0.6.

[0064] 9. The trans-inductor voltage regulator as described in any one of Clauses 1-8, further comprising a second set of switching circuit pairs, the second set of switching circuit pairs comprising: a third set of switching circuits; a third compensating coupling inductor coupled to the third set of switching circuits; a fourth set of switching circuits; and a fourth compensating coupling inductor coupled to the fourth set of switching circuits; wherein the third compensating coupling inductor comprises a first winding of a second compensating coupling transformer, and the fourth compensating coupling inductor comprises a second winding of the second compensating coupling transformer.

[0065] 10. A trans-inductor voltage regulator as described in any one of Clauses 1-9, wherein the fourth compensated coupling inductor is negatively coupled to the third compensated coupling inductor.

[0066] 11. The transinductor voltage regulator as described in any one of clauses 1-10, wherein: the first switch circuit pairing includes a first number of phases, the second switch circuit pairing includes a second number of phases, and the first number of phases is different from the second number of phases.

[0067] 12. The trans-inductor voltage regulator as described in any one of Clauses 1-11, further comprising: a third set of switching circuits; a first compensation inductor connected to the third set of switching circuits; a fourth set of switching circuits; and a second compensation inductor connected to the fourth set of switching circuits.

[0068] 13. In various embodiments, a system includes: a first processor; and a first transinductor voltage regulator that generates a first voltage to the first processor, the first transinductor voltage regulator including: a first switch circuit pairing, the first switch circuit pairing including: a first set of switch circuits; a first compensation coupling inductor coupled to the first set of switch circuits; a second set of switch circuits; and a second compensation coupling inductor coupled to the second set of switch circuits, wherein the first compensation coupling inductor includes a first winding of a compensation coupling transformer, and the second compensation coupling inductor includes a second winding of the compensation coupling transformer.

[0069] 14. The system as described in Clause 13, wherein the second compensated coupling inductor is negatively coupled to the first compensated coupling inductor.

[0070] 15. The system as described in Clause 13 or 14, wherein the second compensating coupling inductor is positively coupled to the first compensating coupling inductor.

[0071] 16. The system of any one of claims 13-15, further comprising: a second transinductor voltage regulator that generates a second voltage to a semiconductor different from the first processor, the second transinductor voltage regulator comprising: a second switch circuit pairing, the second switch circuit pairing comprising: a third set of switch circuits; a third compensation coupling inductor coupled to the third set of switch circuits; a fourth set of switch circuits; and a fourth compensation coupling inductor coupled to the third set of switch circuits; wherein the third compensation coupling inductor is a first winding of a second compensation coupling transformer, and the fourth compensation coupling inductor is a second winding of the second compensation coupling transformer.

[0072] 17. The system of any one of Clauses 13-16, wherein the fourth compensating coupling inductor is negatively coupled to the third compensating coupling inductor.

[0073] 18. The system of any one of Clauses 13-17, wherein the semiconductor comprises one of a central processing unit (CPU), a graphics processing unit (GPU), or an application-specific integrated circuit (ASIC).

[0074] 19. The system of any one of Clauses 13-18 further comprises: a first converter for a first phase, the first converter including a first switching network and a first coupling transformer having a first primary coupling winding and a second secondary coupling winding; and a second converter for a second phase, the second converter including a second switching network and a second coupling transformer having a second primary coupling winding and a second secondary coupling winding, wherein the first secondary coupling winding and the second secondary coupling winding are connected in series.

[0075] 20. The system of any one of Clauses 13-19, wherein the first compensating coupling inductor is connected in series with the first primary winding and the second primary winding.

[0076] Any and all combinations of any claim element recited in any claim and / or any element described in this application fall within the intended scope of this invention and protection in any way.

[0077] The various embodiments have been presented for illustrative purposes and are not intended to be exhaustive or limited to the disclosed embodiments. Many modifications and variations will be apparent to those skilled in the art without departing from the scope and spirit of the described embodiments.

[0078] Various aspects of this embodiment can be embodied as a system or method. Any hardware technology, process, function, component, engine, module, or system described in this disclosure can be implemented as a circuit or circuit set.

[0079] The foregoing description refers to flowchart illustrations and / or block diagrams of methods and apparatus (systems) according to various embodiments of the present disclosure. It should be understood that each block in the flowchart illustrations and / or block diagrams, and combinations of blocks in the flowchart illustrations and / or block diagrams, can be implemented by various parts of the system. It should also be noted that in some alternative implementations, the functions indicated in the blocks may not occur in the order shown in the figures. For example, depending on the functions involved, two blocks shown consecutively may actually be executed substantially concurrently, or these blocks may sometimes be executed in reverse order. It should also be noted that each block in the block diagrams and / or flowchart illustrations, and combinations of blocks in the block diagrams and / or flowchart illustrations, can be implemented by a dedicated hardware-based system that performs the specified function or action.

[0080] While the foregoing relates to various embodiments of this disclosure, other and further embodiments of this disclosure may be contemplated without departing from its essential scope, and the scope of such embodiments is defined by the following claims.

Claims

1. A trans-inductor voltage regulator, comprising: The first switch circuit group pairing includes: First set of switching circuits; A first compensation coupling inductor is coupled to the first set of switching circuits; The second set of switching circuits; and A second compensating coupling inductor is coupled to the second set of switching circuits. The first compensation coupling inductor includes the first winding of the compensation coupling transformer, and the second compensation coupling inductor is the second winding of the compensation coupling transformer.

2. The trans-inductor voltage regulator of claim 1, wherein the second compensated coupling inductor is negatively coupled to the first compensated coupling inductor.

3. The trans-inductor voltage regulator of claim 1, wherein the second compensated coupling inductor is positively coupled to the first compensated coupling inductor.

4. The trans-inductor voltage regulator of claim 1, wherein the first set of switching circuits includes a multiphase converter, the multiphase converter comprising at least: A first converter for a first phase, the first converter including a first switching network and a first coupling transformer; as well as A second converter for the second phase, the second converter including a second switching network and a second coupling transformer.

5. The trans-inductor voltage regulator as described in claim 4, wherein: The first coupling transformer includes a first primary coupling winding and a second secondary coupling winding. The second coupling transformer includes a second primary coupling winding and a second secondary coupling winding, and The first-stage coupling winding and the second-stage coupling winding are connected in series.

6. The trans-inductor voltage regulator of claim 4, wherein the first compensation coupling inductor is connected in series with the first primary winding and the second primary winding.

7. The trans-inductor voltage regulator of claim 1 further includes a feedback network that receives outputs from the first set of switching circuit pairs during operation and generates a feedback signal, the feedback signal being transmitted to the first set of switching circuits and the second set of switching circuits.

8. The trans-inductor voltage regulator of claim 1, wherein the compensation coupling transformer has a self-inductance in the range of 350-450nH and a coupling coefficient in the range of 0.4-0.

6.

9. The trans-inductor voltage regulator as claimed in claim 1, further comprising: The second switching circuit group pairing includes: The third set of switching circuits; A third compensating coupling inductor is coupled to the third set of switching circuits; The fourth set of switching circuits; and A fourth compensating coupling inductor is coupled to the fourth set of switching circuits; The third compensating coupling inductor includes the first winding of the second compensating coupling transformer, and the fourth compensating coupling inductor includes the second winding of the second compensating coupling transformer.

10. The trans-inductor voltage regulator of claim 9, wherein the fourth compensated coupling inductor is negatively coupled to the third compensated coupling inductor.

11. The trans-inductor voltage regulator as claimed in claim 9, wherein: The first switch circuit pairing includes a first phase number. The second switching circuit pairing includes a second number of phases, and The number of the first phase is different from the number of the second phase.

12. The trans-inductor voltage regulator as claimed in claim 1, further comprising: The third set of switching circuits; A first compensation inductor is connected to the third set of switching circuits; The fourth set of switching circuits; as well as The second compensation inductor is connected to the fourth set of switching circuits.

13. A system comprising: First processor; as well as A first transinductor voltage regulator generates a first voltage for the first processor. The first transinductor voltage regulator includes: The first switch circuit group pairing includes: First set of switching circuits; A first compensation coupling inductor is coupled to the first set of switching circuits; The second set of switching circuits; and A second compensating coupling inductor is coupled to the second set of switching circuits. The first compensation coupling inductor includes the first winding of the compensation coupling transformer, and the second compensation coupling inductor includes the second winding of the compensation coupling transformer.

14. The system of claim 13, wherein the second compensated coupling inductor is negatively coupled to the first compensated coupling inductor.

15. The system of claim 13, wherein the second compensating coupling inductor is positively coupled to the first compensating coupling inductor.

16. The system of claim 13, further comprising: A second transinductor voltage regulator generates a second voltage to a semiconductor different from the first processor. The second transinductor voltage regulator includes: The second switching circuit group pairing includes: The third set of switching circuits; A third compensating coupling inductor is coupled to the third set of switching circuits; The fourth set of switching circuits; and A fourth compensating coupling inductor is coupled to the third set of switching circuits; The third compensating coupling inductor is the first winding of the second compensating coupling transformer, and the fourth compensating coupling inductor is the second winding of the second compensating coupling transformer.

17. The system of claim 16, wherein the fourth compensating coupling inductor is negatively coupled to the third compensating coupling inductor.

18. The system of claim 16, wherein the semiconductor comprises one of the following: a central processing unit (CPU), a graphics processing unit (GPU), or an application-specific integrated circuit (ASIC).

19. The system of claim 13, further comprising: A first converter for a first phase, the first converter including a first switching network and a first coupling transformer, the first coupling transformer having a first primary coupling winding and a second secondary coupling winding; as well as A second converter for the second phase, the second converter including a second switching network and a second coupling transformer, the second coupling transformer having a second primary coupling winding and a second secondary coupling winding. The first-stage coupling winding and the second-stage coupling winding are connected in series.

20. The system of claim 13, wherein the first compensating coupling inductor is connected in series with the first primary winding and the second primary winding.

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