Voltage / current or current / voltage conversion system.

Abstract

The present invention relates to a voltage / current or current / voltage conversion system comprising input terminals (31, 32) and output terminals (41, 42), between which there are provided a first set (1) and a second set (2), each of these sets comprising at least one switching cell (11, 21), at least one switching cell of the first set and at least one switching cell of the second set being paired such that each switching cell of the first set is associated with a single switching cell of the second set, and for each pair of switching cells, when the first switch (211) of the switching cell of the second set of the pair is on, the first switch (111) of the switching cell of the first set of the pair is off, and vice versa, and a control device configured and / or programmed to send a signal to the switches of the switching cells to switch the switches between their on state and their off state at the same switching frequency for all the switches.

Description

Technical Field

[0001] The present invention relates to voltage-current or current-voltage conversion systems. The present invention also relates to a method for converting a voltage to a current or a current to a voltage.

[0002] The field of the present invention is more specifically, but not limited to, the field of voltage-current or current-voltage conversion of electromagnetic power supplies in particle accelerators.

Background Art

[0003] By design, switched-mode electronic devices cause current ripple that can be harmful to the load powered by the converter. This is a problem, for example, for electromagnetic power supplies in particle accelerators that must provide a current that is very low in ripple and completely smooth.

[0004] The object of the present invention is to reduce this current ripple as much as possible without reducing the (dynamic) bandwidth of the system. In fact, achieving high variability using an example of a power supply for a particle accelerator is another essential condition for the proper operation of the beam position correction system.

[0005] The most widespread filtering solutions are based on passive elements (capacitors and inductors), and active filter solutions in which transistors operate in the linear mode are also used.

[0006] In passive filtering, in order to achieve a high dynamic range (and at the same time a very good filtering level), it is necessary to increase the switching frequency of the power switch. This reduces the size (and volume) of the output filter of the converter. This results in a decrease in converter efficiency, and in particular an increase in switching losses (due to switching) by the power semiconductors. In order to limit their temperature and maximize their reliability, it may be necessary to supersize the heat sinks to which they are attached. Furthermore, parasitic elements inherent to the components that perform the filtering limit the effective frequency range of the filter. At switching frequencies above several hundred kHz (when very fast switching semiconductors are used), it becomes much more difficult to achieve good electromagnetic compatibility (EMC). To limit this increase in the switching frequency, it is possible to use high-order filters (usually of order 5) obtained by combining several passive filtering cells. These filters, which are calculated to provide equivalent attenuation at the switching frequency compared to lower-order filters, have a higher switching frequency and meet high variability constraints. Another solution for limiting the switching frequency is to use the so-called "interleaving" technique for semiconductor control. The general idea is to combine N switching cells in parallel and drive them with control signals that are phase-shifted from each other by 2π / N. In this way, the apparent frequency "seen" in the load is equal to N times the switching frequency of each cell, thus reducing the size of the output filter and achieving high bandwidth and good efficiency. One of the drawbacks of this method is managing the balance between the currents generated by the N switching cells operating in parallel. An additional control loop may be required to ensure this balancing.

[0007] Generally speaking, passive components and / or coolers occupy a significant proportion of the total volume of the converter.

[0008] However, the linear-mode active filter significantly degrades the overall performance. Furthermore, despite not using passive components, the impact on the overall volume and weight of the converter is significant. In fact, the cooling system associated with the active components also takes up space.

[0009] Therefore, an object of the present invention is to minimize current ripple while performing the following in a voltage-current or current-voltage conversion system or method. -(Dynamic) bandwidth reduction minimization, and / or -Maintaining high variability, and / or -Limiting the reduction in converter efficiency, and / or -Limiting dissipation losses, and / or -Limiting the weight or volume of the converter, and / or -Reducing the weight and volume of passive components and / or coolers, and / or -Not requiring additional control loops to ensure balancing, and / or -Obtaining lower residual levels.

Disclosure of the Invention

[0010] This object is achieved by the following voltage-current or current-voltage conversion system. The system comprises several (typically just two or three) input terminals and several (typically just two or three) output terminals, and between the input terminals and the output terminals, -A first set and a second set, each of the first set and the second set comprising at least one switching cell, comprising, -The system further comprises a common control device for the first set and the second set, -Each switching cell ○Can be in an on state or an off state, a first switch comprising a transistor, ○ can be in an on state or an off state, and a second switch comprising a transistor and / or a diode, comprising whereby, for each switching cell, the switching cell oscillates between two states, namely a first state in which the first switch is on when the second switch is off and a second state in which the first switch is off when the second switch is on, - the number of switching cells in the system is even, - each of the first set and the second set comprises the same number of switching cells (preferably at least one, more preferably exactly one or two or three), - at least one switching cell of the first set is paired with at least one switching cell of the second set such that each switching cell of the first set is associated with a single switching cell of the second set and each switching cell of the second set is associated with a single switching cell of the first set, The control device is configured and / or programmed to send a signal configured to switch the switches between their on and off states at the same switching frequency (F dec ) to the switches of the switching cells, whereby, for each pair of switching cells, when the first switch of the switching cell of the second set of the pair is on, the first switch of the switching cell of the first set of the pair is off, and when the first switch of the switching cell of the second set of the pair is off, the first switch of the switching cell of the first set of the pair is on.

[0011] Each switching cell of the second set can be connected to one of the output terminals or one of the input terminals via an inductor and a capacitor, - the capacitor is configured to suppress the DC current component, and / or - the inductor and the capacitor are 100xF cfa<F dec such that the switching frequency F dec is significantly lower than the switching frequency F cfa to form a high-pass filter having the same.

[0012] The first set and the second set of switching cells may form a four-quadrant chopper structure as a whole.

[0013] The two sets can be connected in parallel between the input terminal and the output terminal, - the first set includes a main converter, and each switching cell of the first set is a switching cell of the main converter, - the second set includes a switched-mode active compensator, and each switching cell of the second set is a switching cell of the switched-mode active compensator.

[0014] The switching cells of the main converter may have the same structure as the switching cells of the compensator.

[0015] The main converter switching cells may have a series chopper structure, and the compensator switching cells may have a series chopper structure.

[0016] The main converter switching cells may have a two-quadrant chopper structure, and the compensator switching cells may have a two-quadrant chopper structure.

[0017] The main converter switching cells may have a four-quadrant chopper structure, and the compensator switching cells may have a four-quadrant chopper structure.

[0018] The main converter switching cells may have a "boost chopper" structure, and the compensator switching cells may have a "boost chopper" structure.

[0019] The main converter switching cell may be designed as a buck-boost chopper, and the compensator switching cell may be designed as a buck-boost chopper.

[0020] The second set may be configured to generate a current ripple with an average value of 0 that has the same amplitude as that generated by the first set but an opposite phase.

[0021] Two first switches of the same pair of switching cells may be connected to the same input and output terminals without passing through a transistor or a switch.

[0022] Two second switches of the same pair of switching cells may be connected to the same input and output terminals without passing through a transistor or a switch.

[0023] Preferably, the switching cell is not connected to the input terminal via a transistor.

[0024] Preferably, the switching cell is not connected to the output terminal via a transistor.

[0025] Each switching cell may be connected to both input terminals without an intermediate element.

[0026] Each switching cell may be connected to one of the output terminals without an intermediate element.

[0027] Each switching cell may be connected to one of the output terminals via an inductor.

[0028] Each switching cell of the first set may be connected to one of the output terminals via only an inductor.

[0029] Each switching cell of the second set may be connected to one of the output terminals via an inductor and a capacitor.

[0030] Each switching cell may be connected to both output terminals without an intermediate element.

[0031] Each switching cell may be connected to one of the input terminals without an intermediate element.

[0032] Each switching cell may be connected to one of the input terminals via an inductor.

[0033] Each switching cell of the first set may be connected to one of the input terminals via only an inductor.

[0034] Each switching cell of the second set may be connected to one of the input terminals via an inductor and a capacitor.

[0035] Each inductor of the first set may be coupled to the inductor of the second set.

[0036] The switching cell transistor may include a MOSFET and / or an IGBT and / or a GaN FET transistor.

[0037] According to yet another aspect of the present invention, a method for controlling a system according to the present invention is proposed, the method comprising common control of a first set and a second set by a control device transmitting to the switches of the switching cells a signal for switching the on-state and the off-state of the switches at the same switching frequency for all switches, whereby, - for each switching cell, the switching cell oscillates between two states, namely a first state in which its first switch is on when its second switch is off and a second state in which its first switch is off when its second switch is on, - For each pair of switching cells, when the first switch of the second set of switching cells in the pair is on, the first switch of the first set of switching cells in the pair is off, and when the first switch of the second set of switching cells in the pair is off, the first switch of the first set of switching cells in the pair is on. It is characterized by this.

[0038] Each switching cell of the second set can be connected to one of the output terminals or one of the input terminals via an inductor and a capacitor. - This capacitor suppresses the DC current component and / or - This inductor and capacitor form a high-pass filter having a switching frequency F that is much lower than the switching frequency F such that it becomes 100xF. cfa <F dec The switching frequency F dec is much lower than the switching frequency F. cfa It forms a high-pass filter having a switching frequency F that is much lower than the switching frequency F such that it becomes 100xF.

[0039] Preferably, the second set generates a current ripple that has the same amplitude as that generated by the first set but has an opposite phase. Other advantages and features will become apparent from the following accompanying drawings upon consideration of the detailed description of the completely non-limiting embodiments and implementations.

Brief Description of the Drawings

[0040]

Figure 1

Figure 2

Figure 3

Figure 4

Figure 5

Figure 6

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Figure 8

Figure 9

Figure 10

Figure 11

Figure 12

Figure 13

Figure 14

DETAILED DESCRIPTION OF THE INVENTION

[0041] These embodiments are in no way limiting, and in particular, considering variants of the invention that include only the selection of the features disclosed below, separated from the other disclosed features, is possible if this selection of features provides a technical advantage or is sufficient to distinguish the invention from the prior art (even if the selection is separated within a clause that includes other features). This selection includes at least one, preferably functional, feature that lacks structural details and / or, if part of the structural details provides a technical advantage or is sufficient to distinguish the invention from the state of the prior art, this feature has only part of this structural detail.

[0042] Very generally, a static converter is a connecting device between an electrical energy source 300 and a load 400. Thus, its main purpose is to control the transfer of energy between the power source and the load. A group of various conversions includes, in particular, choppers that perform direct current - direct current (DC - DC) conversion, inverters that perform direct current - alternating current (DC - AC) conversion, and rectifiers that perform alternating current - direct current (AC - DC) conversion. These forms (DC - DC), (DC - AC), (AC - DC) are all applicable to the present invention.

[0043] The concept of efficiency is of utmost importance, and the losses of the conversion device must be minimized, which theoretically means the use of non - dissipative elements. That is, - switches made using semiconductor components, which have two static states: on and off, - passive and purely receptive components such as capacitors, transformers, and inductors, which are used especially for temporary energy storage and filtering.

[0044] As will be described below, each of the embodiments described below includes a voltage-current or current-voltage conversion system. The system includes input terminals 31, 32 and output terminals 41, 42, and includes the following between the input terminals 31, 32 and the output terminals 41, 42. - A first set 1 and a second set 2, each of the first set and the second set including at least one switching cell.

[0045] Each of the embodiments described below further includes a common control device 3 for the first set 1 and the second set 2.

[0046] The essential structure of the static converter, hereinafter referred to as "switching cells" 11, 12, 21, 22, can be linked to each other like basic components. The simplest "switching cell" conversion structure necessarily uses two switches (K1 and K2 in FIG. 14) whose functions are linked, and their states are necessarily complementary. When one is on, the other is off. This basic structure is called a "switching cell".

[0047] The switching cells 11, 12, 21, 22 typically include three terminals. That is, - A first switch K1 (hereinafter referred to as 111, 121, 211 or 221) connects the first terminal 91 to the second terminal 92 - A second switch K2 (hereinafter referred to as 112, 122, 212 or 222) connects the third terminal 93 to the second terminal 92. - The first switch K1 and the second switch K2 connect the first terminal 91 to the third terminal 93 in series.

[0048] These two switches cannot be closed (i.e., turned on) simultaneously when connected to a voltage source (however, they can be opened simultaneously). Otherwise, a short circuit will occur and the device will be damaged. Similarly, when the cell is connected to a current source, both switches cannot be opened simultaneously (i.e., put them in the off state). However, it is possible to close them simultaneously.

[0049] The second set 2 is designed to generate a current ripple with an average value of 0, which has the same amplitude as that generated by the first set 1 but with the opposite phase. (In the case of a variation of current-voltage conversion, the active compensator filters the current at this time at the system input (not at the output as in the case of voltage-current conversion) and also generates a current ripple with the opposite phase to that of the main converter.)

[0050] As can be seen below, each of the system embodiments according to the present invention described below comprises the following. - At least one inductor L, L1, L2, L3 is provided downstream (in the case of a "step-down" system) or upstream (in the case of a "rectifier" system) of the switching cells of the first set 1 and / or the second set 2. Each of these inductors is a so-called main inductor configured to limit current fluctuations, and each of these main inductors is separate, i.e., not connected in series with a capacitor, and is electrically connected between the switching cells of the first or second set (only the first set 1 for all figures except FIGS. 1 and FIG. 4d) and one of the outputs 41, 42, 43 (in the case of a "step-down" system) and / or one of the inputs 31, 32, 33 (in the case of a "rectifier" system). - At least one so-called filtering inductor L belonging to a high-pass filter is provided downstream (in the case of a "step-down" system) or upstream (in the case of a "rectifier" system) of the switching cells of the first set 1 and / or the second set 1. FA 、L FA1 、L FA2 、L FA3 Each of these filtering inductors is provided with so-called filtering capacitors C FA 、C A1 、C FA2 and C FA3is connected in series, and each of these high-pass filters is electrically arranged between a first set 1 and / or a second set 2 of switching cells (only the second set 2 for all figures except Figures 1 and 4d) and one of the outputs 41, 42, 43 (in the case of a "step-down" system) or one of the inputs 31, 32, 33 (in the case of a "rectifier" system).

[0051] In the figure, C indicates the open (C = 0 on state) and closed (C = 1 off state or closed state) commands of each transistor,

Number

Number

Number

[0052] Filtering capacitors (C FA , C FA1 , C FA2 and C FA3 ) suppress the DC component of the compensator output current. The current ripples of the compensator and the main converter are completely symmetric with respect to the horizontal axis, which makes it possible to cancel almost all of the ripples in the converter output current (this output current is approximately equal to the sum of the current generated by the compensator and the current supplied by the main converter in the first approximation). In this way, the size of the output filter of the main converter can be reduced, and high variability constraints can be satisfied. Furthermore, since the average current through the compensator inductor is 0, the losses generated in the inductor are small.

[0053] Filtering capacitors (C FA , C FA1 , C FA2 and C FA3) does not connect the two terminals 41, 42 to each other, or the two terminals 31, 32 to each other (or at least not directly connect them, or not connect them without passing through its filtering inductor L FA 、L FA1 、L FA2 、L FA3 respectively, and / or not connect them without passing through the switching cell).

[0054] A capacitor C add (not shown) that directly connects the two terminals 41, 42 to each other, or the two terminals 31, 32 to each other, can be added to the present embodiment of the present invention shown in all the figures. However, its technical function is different from that of the filtering capacitors (C FA 、C FA1 、C FA2 and C FA3 respectively) due to its position. Such an additional filtering capacitor C add has the following technical functions. ■ Since the inductance values of the compensator and the main converter are never exactly the same, the compensation is never complete. The capacitor C add removes the residual ripple. ■ Using this capacitor C add , it is also possible to filter out high-frequency disturbances (far exceeding the switching frequency) caused by the switching of the switch to obtain complete electromagnetic compatibility.

[0055] Referring to FIG. 1, a first embodiment of a system 101 according to the present invention is first described, which is a voltage-current conversion system 101 including input terminals 31, 32 (two in the case of FIG. 1) respectively connected to the terminals of a power supply 300 and output terminals 41, 42 (two in the case of FIG. 1) respectively connected to the terminals of a load 400.

[0056] The system 101 includes the following between both the input terminals 31, 32 and the output terminals 41, 42. - A first set 1 and a second set 2, each of the first set 1 and the second set 2 comprising at least one switching cell 11, 21, and more precisely, in the case of FIG. 1, comprising one switching cell.

[0057] System 101 further comprises a common control device 3 for the first set 1 and the second set 2.

[0058] The control device 3 comprises at least one computer, central processing or computing unit, analog electronic circuit (preferably dedicated), digital electronic circuit (preferably dedicated), and / or microprocessor (preferably dedicated), and / or software means.

[0059] Each switching cell 11, 21 respectively ○ A first switch 111 or 211 that can be in an on state or an off state respectively and comprises a transistor, and ○ A second switch 112 or 212 that can be in an on state or an off state respectively and comprises a transistor and / or a diode, and thereby, for each switching cell 11 or 21, this switching cell oscillates between two states, namely a first state in which it is on when its first switch 111 or 211 is respectively off and its second switch 112 or 212 is respectively off, and a second state in which it is off when its first switch 111 or 211 is respectively on and its second switch 112 or 212 is respectively on, and at this time there may be a transient stage of this cell, during which both of these two switches 111 and 112, or 211 and 212 can be off (however, in no case are both on).

[0060] In the case of FIG. 1 - Switch 111 or 211 comprises a transistor, and this transistor is called "high side" or high potential, and its drain is connected to the positive terminal of voltage source 300 - When switch 112 or 212 includes a transistor, this transistor is referred to as the "low side" or low potential, and its source is connected to the negative terminal or ground of voltage source 300. Referring to FIGS. 1 and 14, each switching cell 11, 21 has - its first terminal 91 electrically connected (preferably in coincidence) to terminal 31, - its third terminal 93 electrically connected (preferably in coincidence) to terminal 32, - its second terminal 92 electrically connected to two output terminals 41, 42.

[0061] In the case of a set with a single switching cell, "each switching cell" of the set means that one switching cell of the set.

[0062] Each transistor of the switching cell typically includes a metal oxide semiconductor field effect transistor (MOSFET) and / or an insulated gate bipolar transistor (IGBT) and / or a gallium nitride field effect transistor (GaN FET).

[0063] The on state of the switch is a state in which current can flow through the switch.

[0064] The off state of the switch is a state in which current cannot flow through the switch.

[0065] The number of switching cells 11, 21 in the system is even and equal to 2.

[0066] Each of the first set 1 and the second set 2 includes the same number (only one in the case of FIG. 1) of switching cells 11, 21.

[0067] At least one switching cell 11 of the first set 1 and at least one switching cell 21 of the second set 2 are paired such that each switching cell 11 of the first set 1 is associated with a single switching cell 21 of the second set 2, and each switching cell 21 of the second set 2 is associated with a single switching cell 11 of the first set 1.

[0068] The control device 3 is configured and / or programmed to send a signal (or command) C or C to the switches 111, 112, 211, 212 of the switching cells 11, 21 to switch the switches 111, 112, 211, 212 between their on and off states (and / or vice versa) at the same switching frequency (typically between 5 kHz and 500 kHz) for all switches 111, 112, 211, 212, such that for each pair of switching cells 11, 21, when the first switch 211 of the switching cell 21 of the second set of the pair is on, the first switch 111 of the switching cell 11 of the first set of the pair is off, and when the first switch 211 of the switching cell 21 of the second set of the pair is off, the first switch 111 of the switching cell 11 of the first set of the pair is on, and there may be a transient phase for this pair during which these two first switches 111, 211 can both be off (but in no case are they both on).

[0069] In other words, the control device 3 is configured and / or programmed to send the following for each pair of switching cells 11, 21. - A signal (or command), C or

Number

[0070] Therefore, power electronics is switching electronics (ideally, the on-off switch does not dissipate energy). The switching frequency of this switch is called the "switching frequency". In each switching cycle, a specific amount of energy is transferred between the power supply 300 and the load 400. The control of the energy transfer between the power supply 300 and the load 400 is achieved by adjusting the conduction time of the switch. Therefore, in each switching cell, at least one of the two switches must be controllable (on and / or off). A transistor (e.g., MOSFET) is a switch that can control or monitor the on-off state.

[0071] In the case of FIG. 1, the first set 1 and the second set of switching cells 11, 21 can form a four-quadrant chopper structure as a whole.

[0072] The second set 2 is configured to generate a current ripple having the same amplitude as that generated by the first set 1 but with an opposite phase.

[0073] The same pair of two first switches 111, 211 of the switching cells 11, 21 are electrically connected as follows. - Connected to the same input terminal 31 via the terminal 91 of each cell without passing through the transistors or switches 111, 211, 112, 212 (or capacitors or inductors) - Connected to the same output terminals 41, 42 via the terminal 92 of each cell without passing through the transistors or switches 111, 211, 112, 212, but passing through the following. - Connected to the output 41 through the main inductor L1 of the cell 21 · The filtering inductor L of the cell 11 FA1 (and the filtering capacitor CFA1 ) is connected to output 41 through · Filtering inductor L of cell 21 FA2 (and filtering capacitor C FA2 ) is connected to output 42 through · Is connected to output 42 through main inductor L2 of cell 11

[0074] The same two second switches 112, 212 of the switching cells 11, 21 are electrically connected as follows. - Is connected to the same input terminal 32 through the terminal 93 of each cell without passing through a transistor or a switch (or a capacitor or an inductor), - Is connected to the same output terminals 41, 42 through the terminal 92 of each cell without passing through a transistor or a switch, but through the following. - Is connected to output 41 through the main inductor L1 of cell 21 · Filtering inductor L of cell 11 FA1 (and filtering capacitor C FA1 ) is connected to output 41 through · Filtering inductor L of cell 21 FA2 (and filtering capacitor C FA2 ) is connected to output 42 through · Is connected to output 42 through the main inductor L2 of cell 11

[0075] The switching cells 11, 21 are not electrically connected to the input terminals 31, 32 through a transistor.

[0076] The switching cells 11, 21 are not electrically connected to the output terminals 41, 42 through a transistor.

[0077] Each switching cell 11, 21 is electrically connected to both input terminals 31, 32 without an intermediate element.

[0078] Each switching cell 11, 21 - Electrically connected to one of the output terminals 41 or 42 via the main inductor - Electrically connected to each of the other of the output terminals 42 or 41 via a filtering inductor in series with a filtering capacitor.

[0079] Each switching cell 11, 21 is electrically connected to one of the output terminals 41, 42 via an inductor.

[0080] Each switching cell 11 of the first set 1 is electrically connected to one output terminal 42 only via the main inductor L2.

[0081] Each switching cell 21 of the second set 2 is the filtering inductor L FA2 and the filtering capacitor C FA2 Only electrically connected to one output terminal 42 via.

[0082] All the modifications considered in this specification, the power supply 300 at the input terminals 31, 32 is a DC voltage source (such as a battery, the output filtered by a capacitor of an AC-DC converter, etc.).

[0083] The load 400 at the output terminals 41, 42 can be, for example, DC power (such as a battery, an MCC type rotating machine, an electromagnet, etc.), or any type of device that typically requires low-frequency power of less than 1 kilohertz (such as grid injection, an AC rotating machine, an electromagnet, etc.).

[0084] In the case of system 101, the main converter groups the first set 1 and the second set 2 as a whole to form a four-quadrant chopper, and the structure of system 101 is simplified compared to systems 102, 103, 104 described later (an auxiliary converter is not required).

[0085] L1, L FA1 、C FA2 Are part of the second set 2.

[0086] L2, L FA1 , C FA1 are part of the first set 1.

[0087] Referring to FIGS. 2a, 3a, 3b, and 3c, further embodiments of the systems 102, 103, 104 according to the present invention will be described, but only with respect to differences from the system 101, which is also a voltage-current conversion system having input terminals 31, 32 (two in the case of FIGS. 2a, 3a, 3b, 3c) and output terminals 41, 42 (two in the case of FIGS. 2a, 3a, 3b, 3c).

[0088] In all of these systems 102, 103, or 104, the two sets 1, 2 are connected in parallel between the input terminals 31, 32 and the output terminals 41, 42. That is, - The first set 1 includes a main converter 61 having all the switching cells of the first set 1, and each switching cell 11, 12 of the first set is a switching cell of the main converter - The second set (2) includes a switched-mode active compensator 62 having all the switching cells of the second set 2, and each switching cell 21, 22 of the second set is a switching cell of the switched-mode active compensator.

[0089] Main inductors L, L1, L2, etc. are part of the first set 1.

[0090] Filtering inductors L FA , L FA1 , L FA2 etc., and filtering capacitors C FA , C FA1 , C FA2 etc. are part of the second set 2.

[0091] Therefore, the switched-mode active compensator 62 is designed to benefit from the advantages of both passive and active components. The principle of the compensator 62 according to the present invention is thereby to generate a current ripple opposite to the current ripple generated by the main converter 61. By superimposing the main converter current 61 and the compensator current 62, the ripple of the converter 61 is almost canceled. In this way, the size of the output filter of the main converter 61 can be reduced, and high variability constraints can be met.

[0092] Therefore, systems 102, 103 or 104 have the following advantages. · This filtering solution is based on the switched-mode active compensator 62, which significantly reduces the proportion of passive elements in the filter (eliminating the cascaded passive low-pass filtering cells). · The active switching filter operates at a lower switching frequency than the passive filter while ensuring a good bandwidth. · The active compensator 62 does not consume much power and does not impair the overall efficiency of systems 102, 103 or 104. · Easy to use.

[0093] Unlike the active filter related to the common-mode EMC disturbance at the converter input, the active compensator 62 proposed here addresses the disturbance of the differential-mode output current wave (at the switching frequency).

[0094] The main converter 61 is a static converter, preferably with bidirectional current (although a one-way static converter is also possible), and the compensator 62 is the same type of static converter.

[0095] Systems 102, 103 or 104 comprise the following between both the input terminals 31, 32 and the output terminals 41, 42. - A first set 1 and a second set 2, each of the first set 1 and the second set 2 comprising at least one switching cell 11, 12, 21, 22, and more precisely, in the case of FIG. 3a or FIG. 3b, one switching cell, and in the case of FIG. 3c, two switching cells.

[0096] The system 102, 103 or 104 further comprises a common control device 3 for the first set 1 and the second set 2.

[0097] Each switching 11, 21, 12 or 22 respectively ○ Can be in an on state or an off state respectively, and a first switch 111, 211, 121 or 221 comprising a transistor, ○ Can be in an on state or an off state respectively, and a second switch 112, 212, 122 or 222 comprising a transistor and / or a diode, and Thereby, for each switching cell 11, 21, 12 or 22, this switching cell oscillates between two states, namely, a first state in which it is on when its first switch 111, 211, 121 or 221 is respectively off and its second switch 112, 212, 122 or 222 is respectively off, and a second state in which it is off when its first switch 111, 211, 121 or 221 is respectively on and its second switch 112, 212, 122 or 222 is respectively on, and there may be a transient phase of this cell during which these two switches 111 and 112, or 211 and 212, or 121 and 122, or 221 and 222 can both be off (but in no case are both on).

[0098] The number of switching cells 11, 21, 12, or 22 in the system 102, 103, or 104 is even, equal to 2 in FIG. 3a or FIG. 3b, and equal to 4 in FIG. 3c.

[0099] Each of the first set 1 and the second set 2 comprises the same number (one for FIGS. 3a or 3b, or two for FIG. 3c) of switching cells 11, 21, 12, or 22.

[0100] At least one switching cell 11, 12 of the first set 1 and at least one switching cell 21, 22 of the second set 2 are paired such that each switching cell 11 or 12 of the first set 1 is associated with a single switching cell 21 or 22 of the second set 2 respectively, and each switching cell 21 or 22 of the second set 2 is associated with a single switching cell 11 or 12 of the first set 1 respectively.

[0101] The control device 3 is configured and / or programmed to send a signal (or command) C or C to the switches 111, 211, 121, 221, 112, 212, 122, 222 of the switching cells 11, 21, 12 or 22 to switch the switches 111, 211, 121, 221, 112, 212, 122, 222 between their on and off states (and / or vice versa) at the same switching frequency (typically between 5 kHz and 500 kHz) for all switches, whereby for each pair of switching cells (pairs 11, 21 and 12, 22), when the first switch 211 or 221 of each switching cell 21 or 22 of the second set of the pair is on, the first switch 111 or 121 of each switching cell 11 or 12 of the first set of the pair is off, and when the first switch 211 or 221 of each switching cell 21 or 22 of the second set of the pair is off, the first switch 111 or 121 of each switching cell 11 or 12 of the first set of the pair is on, at which time there may be a transient phase for this pair during which these two first switches of this pair can both be off (but in no case both on).

[0102] The second set 2 is configured to generate a current ripple that has the same amplitude as that generated by the first set 1 but with an opposite phase.

[0103] Thus, the electrical circuit diagrams corresponding to systems 102, 103, or 104 comprise the following. - A power supply and its input terminals 31, 32, - A load and its output terminals 41, 42, - A main static converter 61 that serves to transfer electrical energy from the power supply to the load (and vice versa if reversible).

[0104] The active compensator 62 is connected in parallel with the main converter 61. The converter 61 and the compensator 62 are powered by the same power supply and controlled by the same remote control circuit 3. They both operate at the same switching frequency.

[0105] Downstream of the main static converter 61, current fluctuations are restricted by the main inductor L, L1, or L2.

[0106] Downstream of the compensator 62, these fluctuations are restricted by a high-pass filter consisting of filtering capacitors C FA , C FA1 , C FA2 in series with filtering inductors L FA , L FA1 , L FA2 each (having the same value as L, L1, or L2 of the main converter 61).

[0107] The inductors L, L1, L2 located downstream of the converter 61 and the inductors L FA , L FA1 , L FA2 located downstream of the compensator 62 are independent of each other.

[0108] Two first switches 111, 211 or 121, 221 of the same pair in switching cells 11, 21 or 12, 22 are electrically connected to the same input and output terminals without passing through transistors or switches 111, 211, 112, 212.

[0109] More precisely, Two first switches 111, 211 of a pair of one switching cell 11, 21 are electrically connected as follows. ○ Connected to the same input terminal 31 via terminal 91 of each cell without passing through transistors or switches 111, 211, 121, 221, 112, 212, 122, 222 (or without passing through a capacitor or an inductor) ○ In the cases of FIGS. 3a and 3b, without passing through transistors or switches 111, 211, 121, 221, 112, 212, 122, 222 (however, only passing through inductor L or through a capacitor C FA and inductor L in series FA ), connected to the same output terminal 41 via terminal 92 of each cell ○ In the case of FIG. 3c, without passing through transistors or switches 111, 211, 121, 221, 112, 212, 122, 222 (however, only passing through inductor L2 or through a capacitor C FA2 and inductor LFA2 in series with it), connected to the same output terminal 42 via terminal 92 of each cell. In the case of FIG. 3c, two first switches 121, 221 of a pair of switching cells 12, 22 are electrically connected as follows. ○ Connected to the same input terminal 31 via terminal 91 of each cell without passing through transistors or switches 111, 211, 121, 221, 112, 212, 122, 222 (or without passing through a capacitor or an inductor) ○ Without passing through transistors or switches 111, 211, 121, 221, 112, 212, 122, 222 (however, only passing through inductor L1 or through a capacitor C FA1 and inductor L in series FA1through the terminals 92 of each cell to the same output terminal 41 - The two second switches 112 and 212 of the pair of switching cells 11 and 21 are electrically connected as follows. ○ Without passing through the transistors or switches 111, 211, 121, 221, 112, 212, 122, 222 (or without passing through a capacitor or an inductor), they are connected to the same input terminal 32 through the terminals 93 of each cell. ○ In the cases of FIGS. 3a and 3b, without passing through the transistors or switches 111, 211, 121, 221, 112, 212, 122, 222 (however, passing only through the inductor L or the inductor L FA in series with the capacitor C FA through), they are connected to the same output terminal 41 through the terminals 92 of each cell. ○ In the cases of FIGS. 3a and 3b, without passing through the transistors or switches 111, 211, 121, 221, 112, 212, 122, 222 (or without passing through a capacitor or an inductor), they are connected to the same output terminal 42 through the terminals 93 of each cell. ○ In the case of FIG. 3c, without passing through the transistors or switches 111, 211, 121, 221, 112, 212, 122, 222 (however, passing only through the inductor L2 or the inductor L FA2 in series with the capacitor C FA2 through), they are connected to the same output terminal 42 through the terminals 92 of each cell. - In the case of FIG. 3c, the two second switches 122 and 222 of the pair of switching cells 12 and 22 are electrically connected as follows. ○ Without passing through the transistors or switches 111, 211, 121, 221, 112, 212, 122, 222 (or without passing through a capacitor or an inductor), they are connected to the same input terminal 32 through the terminals 93 of each cell. ○ Without passing through the transistors or switches 111, 211, 121, 221, 112, 212, 122, 222 (however, passing only through the inductor L1 or the inductor L FA1 in series with the capacitor C FA1via) the terminals 92 of each cell, are connected to the same output terminal 41

[0110] The same pair of two second switches 112, 212 of the switching cells 11, 21 are not passed through a transistor or a switch, but are optionally electrically connected to the same input terminals 31, 32 and output terminals 41, 42 by an inductor or an inductor and a series capacitor.

[0111] The switching cells 11, 21, 12 or 22 are not electrically connected to the input terminals 31, 32 via a transistor.

[0112] The switching cells 11, 21, 12 or 22 are not electrically connected to the output terminals 41, 42 via a transistor.

[0113] Each switching cell 11, 21, 12, or 22 is electrically connected to both input terminals 31, 32 without an intermediate element.

[0114] Each switching cell 11, 21, 12 or 22 is electrically connected to at least one of the output terminals 41, 42 via an inductor.

[0115] Each switching cell 11, 12 of the first set 1 is electrically connected to one of the output terminals (41 for FIGS. 3a and 3b, 41 or 42 for FIG. 3c) only via the main inductor.

[0116] Each switching cell 21, 22 of the second set 2 is electrically connected to one of the output terminals (41 for FIGS. 3a and 3b, 41 or 42 for FIG. 3c) only via the filtering inductor in series with the filtering capacitor.

[0117] In FIGS. 3a and 3b, each switching cell 11, 21, 12 or 22 is electrically connected to one output terminal 42 without an intermediate element.

[0118] The use of the active filter reduces the size of the passive filtering components used at the output of the main converter 61.

[0119] In the system 102 of a specific case shown in FIG. 3a, the switching cell 11 of the main converter has a series chopper structure, and the switching cell 21 of the compensator 62 has a series chopper structure.

[0120] Both the main converter 61 and the compensator 62 are based on a structure known as a series chopper. In this embodiment, the converter 61 is not current reversible, and the active compensation principle only functions when the average value of the current supplied by the main static converter is greater than half of the ripple of the current flowing through the inductor downstream of the main converter. This is to avoid the so-called discontinuous current state that is reached when the current in the diode is canceled before the end of the switching period.

[0121] In the system 103 of a specific case shown in FIG. 3b, the switching cell 11 of the main converter 61 has a two-quadrant chopper structure, and the switching cell 21 of the compensator 62 has a two-quadrant chopper structure.

[0122] Both the converter 61 and the compensator 62 are based on a structure known as a current-reversible two-quadrant chopper structure.

[0123] In the system 104 of a specific case shown in FIG. 3c, the switching cells 11, 12 of the main converter 61 have a four-quadrant chopper structure, and the switching cells 21, 22 of the compensator 62 have a four-quadrant chopper structure.

[0124] The converter 61, similar to the compensator 62, is based on a structure known as a four-quadrant full-bridge chopper where both current and voltage are reversible.

[0125] In the case of FIG. 3c - Switch 111 or 211 or 121 or 221 includes a transistor, which is called "high side" or "high potential", and its drain is connected to the positive terminal of the voltage source 300. - If switch 112 or 212 or 122 or 222 includes a transistor, this transistor is called "low side" or "low potential", and its source is connected to the negative terminal of the voltage source 300 or ground.

[0126] Referring to FIGS. 3a, 3b, 3c and 14, each switching cell 11, 12, 21, 22 - has its first terminal 91 electrically connected (preferably in coincidence) to the input terminal 31. - has its third terminal 93 electrically connected (preferably in coincidence) to the input terminal 32 (and optionally the output terminal 42). - has its second terminal 92 electrically connected to the output terminal 41 or 42.

[0127] Referring to FIGS. 4d, 2b, 4a, 4b, 4c, further embodiments of the systems 201, 202, 203, 204 according to the present invention will be described here, but only with respect to the differences from the systems of the foregoing figures.

[0128] In these figures, - the system 201 of FIG. 4d corresponds to the system 101 of FIG. 1. - the systems 202 of FIGS. 2b and 4a correspond to the system 102 of FIGS. 2a and 3a. - the systems 203 of FIGS. 2b and 4b correspond to the system 103 of FIGS. 2a and 3b. - the system 204 of FIG. 4c corresponds to the system 104 of FIG. 3c. However, each main inductor L or L1 or L2 of the first set 1 is further coupled to each of the filtering inductors L FA or L FA1 or L FA2 of the second set 2, respectively.

[0129] The inductor L, L1, or L2 located downstream of the converter 61 and the inductor L FA , L FA1 , L FA2 located downstream of the compensator 62 are coupled. More precisely, each main inductor L, L1 or L2 located downstream of the converter 61 is coupled to one of the filtering inductors L FA , L FA1 , L FA2 located downstream of the compensator 62.

[0130] The use of an active filter reduces the size of the passive filtering components used at the output of the main converter 61. This advantage can be enhanced by coupling the main inductor L, L1 or L2 to the inductor L FA , L FA1 , L FA2 located downstream of the active compensator 62.

[0131] Thus, the use of the coupled inductor results in a reduction in the volume of passive components and gives rise to new deformation modes. That is, - the main converter 61 can be considered as a series chopper, like the active compensator 62 (Figure 4-a), or, - the main converter 61 can be considered as a current-reversible two-quadrant chopper, like the active compensator 62 (Figure 4-b), or - the main converter 61 can be considered as a four-quadrant full-bridge chopper, like the active compensator 62 (Figure 4-c), or, - the structure of Figure 4-d is simplified as in the structure of Figure 1.

[0132] All systems 101, 102, 103, 104, 201, 201, 203, 204 are "step-down" systems, i.e., the output voltage is adjustable and is at most equal to the input voltage.

[0133] However, the active compensator may be used in a "step-up" configuration. In this case, instead of compensating for the current ripple at the output of converter 61, compensation is performed on the input current, which can be interesting for certain applications. The dimensions of the corresponding variant of the active compensator are the same as those used in the step-down configuration. These variants offer the same advantages as the previous ones because of their ease of use. They are particularly useful for applications using non-localized power sources such as solar panels and fuel cells, and it is particularly important to filter the disturbances generated by the switching of the power converter with respect to the current supplied by these power sources.

[0134] Therefore, each of these systems 101, 102, 103, 104, 201, 202, 203, 204 can be changed to a respective "step-up" system 301, 302, 303, 304, 401, 402, 403, 404 (referred to herein but not necessarily shown) while remaining within the scope of the present invention by moving the main inductors L, L1, L2, and the filtering inductors L FA 、L FA1 、L FA2 、and the filtering capacitors C FA 、C FA1 、C FA2 to the inputs 31, 32.

[0135] For example, - Figure 5a shows the "step-up" systems 302, 303 according to the present invention and will only be described with respect to the differences from the systems 102, 103 shown in Figure 2a. - Figure 5b shows the "step-up" system 303 according to the present invention and will only be described with respect to the differences from the system 103 shown in Figure 3b.

[0136] The "step-up" systems 302, 303 shown in Figure 5b correspond to the system 103 shown in Figure 3b, with the inductors L, L FA 、and the capacitor C FAis moving to inputs 31, 32. This structure is based on a DC-DC boost converter (also known as a parallel chopper).

[0137] In this case, each switching cell is electrically connected to both output terminals without passing through an intermediate element.

[0138] Each switching cell is electrically connected to one input terminal without passing through an intermediate element.

[0139] Each switching cell is electrically connected to one input terminal via a main inductor or a filtering inductor.

[0140] Each switching cell of the first set is electrically connected to one input terminal only via a main inductor.

[0141] Each switching cell of the second set is electrically connected to one input terminal only via a filtering inductor in series with a filtering capacitor.

[0142] In the case of FIG. 5b, the switching cells of the main converter have a "boost chopper" structure, and the switching cells of the compensator have a "boost chopper" structure.

[0143] Each of these systems 101, 102, 103, 104, 201, 202, 203, 204, 301, 302, 303, 304, 401, 402, 403, 404 can be modified to a three-phase system, i.e., a three-phase system having three input terminals and / or three output terminals.

[0144] For example, FIGS. 6a and 6b show a "buck" system 504 according to the present invention, which is only described with respect to the differences from the system 104 in FIG. 3c. This is only a modification of the system 104 in FIG. 3c to a three-phase with three output terminals. Therefore, the main L3 and the filtering L FA3 inductor and the filtering capacitor C FA3is added before the third output 43.

[0145] Therefore, in addition to the modified forms of the DC-DC converter, the system can also be combined with a three-phase inverter (buck structure) or a rectifier (boost structure). FIG. 6 shows an embodiment of the three-phase inverter. Each inverter arm is associated with a compensation stage. The current ripple limiting component and the compensation inductor must match. The modified form with the inductor coupled remains valid.

[0146] Each arm and its compensation stage provide a path for the current ripple, and thus the current ripple is not transmitted to the load. The capacitor in the compensation stage supports the low-frequency (LF) voltage. The load connection (star or delta) is not important. Each arm is sized for one line current. The compensation stage is sized only for the maximum ripple value.

[0147] Regarding the dimensions, for all the modified forms shown above, it is possible to select, for example, according to the existing elements. -L = L FA or approximately equal, ±20%, ideally ±5% -L1 = L FA1 or approximately equal, ±20%, ideally ±5% -L2 = L FA2 or approximately equal, ±20% ideally ±5% -L3 = L FA3 or approximately equal, ±20%, ideally ±5% -Preferably, L = L1 = L2 = L3 or approximately equal, ±20%, ideally ±5%. The larger the tolerance between the values of L, L1, L2, and L3, the lower the filtering level. -Capacitor C FA , C FA1 , C FA2 , C FA3 are used to reliably filter all harmonics, so that the capacitor and the inductor L FA , L FA1 , L FA2 , LFA3 The switching frequency F of the high-pass filter formed with each cfa is much lower than the switching frequencies F of the main converter and the compensator, i.e., F dec <<F cfa <<F dec , typically 100xF cfa <F dec , and are dimensioned accordingly. - The switching frequency F of the active compensator 62 dec is the same as the switching frequency of the main converter 61. - The active compensator 62 and the main converter 61 share the same control circuit 3 and, to the extent possible, the same type of driver.

[0148] Therefore, a method of controlling any of the embodiments of the system according to the present invention described above is a first set 1 and a second set 2 by the control device 3 sending a signal to the switches of the switching cells to switch the switches between the on state and the off state at the same switching frequency for all switches. Common control, whereby - For each switching cell, the switching cell oscillates between two states, namely, a first state in which the first switch is on when the second switch is off and a second state in which the first switch is off when the second switch is on, - For each pair of switching cells, when the first switches 211, 221 of the switching cells of the second set of the pair are on, the first switches 111, 121 of the switching cells of the first set of the pair are off, and when the first switches 211, 221 of the switching cells of the second set of the pair are off, the first switches 111, 121 of the switching cells of the first set of the pair are on.

[0149] The second set generates a current ripple that has the same amplitude as that generated by the first set but a phase opposite thereto.

[0150] To further illustrate the technical advantages of the present invention over the prior art, a detailed description of a specific signal simulation in an embodiment of the system according to the present invention is provided.

[0151] FIG. 7 shows a system 102 having a series chopper type static converter 61 as shown in FIGS. 2a and 3a.

[0152] Referring to these three figures, -Ve is the converter input voltage 61, -C is the on (C = 0) and off (C = 1) control of the transistor 111 of the main converter 61,

Number

[0153] The corresponding waveforms are shown in FIG. 8 for two switching periods.

[0154] The result was very good compensation. This remains unchanged regardless of the duty cycle value of any switch control signal.

[0155] Figure 9a is an electrical circuit diagram using the PSIM electronic simulation software of the system 103 shown in FIGS. 2a and 3b, and the active compensator 62 is associated with a current reversible two-quadrant chopper.

[0156] Figure 9b shows the verification of some signals (IL1, ILfa, and Icomp specified in FIG. 9a) using the PSIM electronic simulation software of this system 103.

[0157] Figure 10a is an electrical circuit diagram using the PSIM electronic simulation software of the system 303 shown in FIGS. 5a and 5b, and the active compensator 62 is associated with a parallel chopper.

[0158] Figure 10b shows the verification of some signals (IL1, ILfa, and Ie specified in FIG. 10a) using the PSIM electronic simulation software of this system 103.

[0159] Figure 11a is an electrical circuit diagram using the PSIM electronic simulation software of the system 504 shown in FIGS. 6a and 6b, and the active compensator 62 is associated with a three-phase inverter.

[0160] Figure 11b shows the verification of some signals (IL1, IL2, IL3, IComp1, IComp2, IComp3, IFA1, IFA2, IFA3 specified in FIG. 11a) using the PSIM electronic simulation software of this system 103.

[0161] Figure 12 shows a comparison of the transient processes obtained for the system 104 in FIG. 3c having a four-quadrant full-bridge chopper converter at a given load current filtering level, with the reference being 71, with the active compensator 62 being 73, and without it being 72.

[0162] FIG. 13 shows a comparison of the filtering levels obtained for the system 104 of FIG. 3c with a four-quadrant full-bridge chopper converter at a given bandwidth, with the reference being 81, with active compensator being 83, and without being 82.

[0163] Of course, the present invention is not limited to the examples described above, and many adjustments can be made to these examples without exceeding the scope of the present invention.

[0164] All of the foregoing embodiments can be - As shown in the circuit diagram of FIG. 2, for example, it can be modified for current-voltage conversion simply by exchanging the power supply and the load. In this case, the active compensator filters the current this time at the system input (not at the output as in the case of voltage-current conversion) and generates a current ripple in the opposite phase with respect to the main converter. Thus, for example, in FIGS. 1, 3b, 3c, 4b, 4c, 4d, 5b, 6b and their corresponding descriptions, the power supply Vdc or the reference 300 can be generalized to the case of a DC power supply or a load, respectively, and the load or the reference 400 can be generalized to the case of a load or a power supply, respectively (DC or AC in FIG. 1, DC in FIG. 3b, DC or AC in FIG. 3c, DC in FIG. 4b, AC or DC in FIGS. 4c or 4d, AC in FIG. 6). Thus, the present invention can handle cases such as series choppers, boost choppers, single-phase inverters, single-phase rectifiers, etc., and / or - Generalized to n pairs of switching cells or n switching cells per set 1 or 2 (n is a positive natural number). For example, In the case of FIG. 3c, n = 2, but embodiments such as n = 3 and n = 4 can be assumed, and / or - Consider that the same set 1 or 2 of switching cells preferably receive control signals phase-shifted by n between two cells of the same set 1 or 2, or by 2n / n between n cells of the same set 1 or 2. This makes available an apparent load frequency n times greater than the interleaving and switch frequencies, increasing the attenuation of the filter. For example, in the case of n = 2 in FIG. 3c, due to the phase shift of n between cells 11 and 12 (and also between cells 21 and 22), when switches 111 and 112 of cell 11 receive signals C and

Number

Number

Number

[0165] Furthermore, the main converter switching cell may be designed as a buck - boost chopper, and the compensator switching cell may also be designed as a buck - boost chopper.

[0166] Naturally, various features, forms, deformations, and embodiments of the present invention can be combined with each other in various combinations as long as they are not mutually incompatible or exclusive. In particular, all the deformations and embodiments described above can be combined with each other.

Claims

1. A voltage-to-current or current-to-voltage conversion system comprising input terminals (31, 32) and output terminals (41, 42), wherein between the input terminals and the output terminals, - A first set (1) and a second set (2), wherein each of the first set and the second set comprises at least one switching cell (11, 12, 21, 22), Equipped with, - The system further comprises a common control device (3) for the first set and the second set, - Each switching cell is, ○A first switch (111, 121, 211, 221) equipped with a transistor that can be set to an ON or OFF state, ○ A second switch (112, 122, 212, 222) that can be set to an ON or OFF state and comprises a transistor and / or a diode, Equipped with, As a result, each switching cell oscillates between two states: a first state in which the first switch is on when the second switch is off, and a second state in which the first switch is off when the second switch is on. - The number of switching cells in the system is even, - Each of the first set and the second set comprises the same number of the switching cells, - Each switching cell in the first set is associated with a single switching cell in the second set, and each switching cell in the second set is associated with a single switching cell in the first set, such that at least one of the switching cells in the first set and at least one of the switching cells in the second set are associated in pairs. The control device is configured and / or programmed to transmit signals to the switches of the switching cells that cause all the switches to switch between their on and off states at the same switching frequency Fdec, so that for each pair of switching cells, when the first switch (211, 221) of the switching cell in the second set of the pair is on, the first switch (111, 121) of the switching cell in the first set of the pair is off, and when the first switch (211, 221) of the switching cell in the second set of the pair is off, the first switch (111, 121) of the switching cell in the first set of the pair is on.

2. The system according to claim 1, characterized in that the switching cells of the first set and the second set as a whole form a four-quadrant chopper structure.

3. The two sets are connected in parallel between the input terminal and the output terminal. - The first set (1) comprises a main converter, and each switching cell of the first set is a switching cell of the main converter. - The second set (2) comprises a switch-mode active compensator, and each switching cell of the second set is a switching cell of the switch-mode active compensator. The system according to claim 1, characterized in that

4. The system according to claim 3, characterized in that the switching cell of the main converter has a series chopper structure, and the switching cell of the compensator has a series chopper structure.

5. The system according to claim 3, characterized in that the switching cell of the main converter has a two-quadrant chopper structure, and the switching cell of the compensator has a two-quadrant chopper structure.

6. The system according to claim 3, characterized in that the switching cell of the main converter has a four-quadrant chopper structure, and the switching cell of the compensator has a four-quadrant chopper structure.

7. The system according to any one of claims 1 to 6, characterized in that the second set is configured to generate a current ripple having the same amplitude as that generated by the first set but with the opposite phase.

8. The system according to any one of claims 1 to 6, characterized in that the two first switches of the same pair in the switching cell are connected to the same input and output terminals without passing through a transistor or switch.

9. The system according to any one of claims 1 to 6, characterized in that the two second switches of the same pair of switching cells are connected to the same input and output terminals without passing through a transistor or switch.

10. The system according to any one of claims 1 to 6, characterized in that the switching cell is not connected to the input terminal via a transistor.

11. The system according to any one of claims 1 to 6, characterized in that the switching cell is not connected to the output terminal via a transistor.

12. The system according to any one of claims 1 to 6, characterized in that each switching cell is connected to the two input terminals without an intermediate element.

13. The system according to claim 12, characterized in that each switching cell is connected to one of the output terminals without an intermediate element.

14. The system according to claim 12, characterized in that each switching cell is connected to one of the output terminals via an inductor.

15. The system according to claim 12, characterized in that each switching cell of the first set is connected to one of the output terminals only via an inductor.

16. The system according to claim 12, characterized in that each switching cell of the second set is connected to one of the output terminals via an inductor and a capacitor.

17. The system according to any one of claims 1 to 6, characterized in that each switching cell is connected to the two output terminals without an intermediate element.

18. Each switching cell is characterized by being connected to one of the input terminals without an intermediate element. The system according to claim 17.

19. The system according to claim 17, characterized in that each switching cell is connected to one of the input terminals via an inductor.

20. The system according to claim 17, characterized in that each switching cell of the first set is connected to one of the input terminals only via an inductor.

21. The system according to claim 17, characterized in that each switching cell of the second set is connected to one of the input terminals via an inductor and a capacitor.

22. The system according to claim 14, characterized in that each inductor (L1, L2) of the first set is coupled with the inductors (LFA1, LFA2) of the second set.

23. The system according to any one of claims 1 to 6, characterized in that the transistor of the switching cell includes a MOSFET and / or an IGBT and / or a GaN FET transistor.

24. A method for controlling the system according to any one of claims 1 to 6, the method comprising common control of the first set and the second set by the control device (3) transmitting a signal to the switches of the switching cell to switch all of the switches between the on state and the off state of the switches at the same switching frequency, thereby, - For each switching cell, this switching cell oscillates between two states: a first state in which the first switch is on when the second switch is off, and a second state in which the first switch is off when the second switch is on. - For each pair of switching cells, when the first switch (211, 221) of the switching cell in the second set of the pair is ON, the first switch (111, 121) of the switching cell in the first set of the pair is OFF, and when the first switch (211, 221) of the switching cell in the second set of the pair is OFF, the first switch (111, 121) of the switching cell in the first set of the pair is ON. A method characterized by the following features.

25. The method according to claim 24, characterized in that the second set generates a current ripple having the same amplitude as that generated by the first set but with the opposite phase.

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