DC-to-DC converter

Abstract

The invention relates to a DC-to-DC converter (1) comprising an input (10), an output (20) and a converter circuit (30) between the input (10) and the output (20), said converter circuit having a controllable switch (T1), which is designed as a semiconductor switch, and an energy store (L1), which can be cyclically charged and discharged by switching on and off the switch (T1). The DC-to-DC converter also comprises a control device (40) in order to monitor the input voltage (VBR), the output voltage (Vboost), a voltage (Vzvd) applied to the switch (T1), and a current (Ids) flowing through the switch (T1) in order to determine, on the basis of the result of the monitoring process, the points in time (ton, toff) at which the switch (T1) is switched on and switched off and in order to control the switch (T1). In order to allow the converter (1) to be provided cost-effectively while nevertheless being flexibly adaptable to specific applications, the control device (40) is implemented, according to the invention, by means of a microcontroller module comprising a peripheral device (43) connected to the converter circuit (30), a simulation of the current (Ids) flowing through the switch (T1) being provided by means of the microcontroller module so as to monitor the current (Ids) in order to determine the current (Ids) while taking into account the result of the monitoring process for one or more of the aforementioned voltages (VBR, Vboost, Vzvd).

Description

[0001] Description

[0002] DC / DC converter

[0003] The present invention relates to a DC-DC converter. The invention further relates to a use of the DC-DC converter and a computer program product.

[0004] DC / DC converters are known to comprise an input for supplying an input voltage, an output for outputting an output voltage, and a converter circuit functionally arranged between the input and output.

[0005] The converter circuit, supplied with the input voltage, transfers electrical energy from the input to the output, generating either a higher output voltage (boost conversion) or a lower output voltage (step-down conversion) relative to the input voltage. This type of converter circuit comprises a controllable switch (e.g., MOSFET) designed as a semiconductor switch and an energy storage device (e.g., inductor or capacitor) that can be cyclically charged and discharged by alternating the switching on and off of this switch (typically in the kHz range) to accomplish the voltage conversion. Various converter topologies suitable for such circuits are known from the prior art of so-called switching regulators (e.g., "boost converter," "flyback converter," "sepic converter," etc.).

[0006] Finally, such a known DC-DC converter includes, as a further part of the circuit arrangement forming the DC-DC converter, a control device, e.g. an application-specific integrated circuit (ASIC), which continuously monitors the input voltage, the output voltage, a voltage applied to the switch, and a current flowing through the switch during operation of the DC-DC converter in order to determine the times for switching on and off the switch according to a predetermined switching strategy, depending on the result of this monitoring, and to control the switch accordingly.

[0007] In this context, the term "monitoring" of a voltage or current includes, in particular, for example, the measurement of the quantity in question. However, such monitoring can also be implemented, for example, as the detection of whether the quantity in question exceeds or falls below a predetermined threshold.

[0008] Regarding the determination of the switching times, various "switching strategies" are possible, depending on the specific converter topology used. Each strategy defines suitable switching times based on the results of the aforementioned monitoring. Such a switching strategy is essential for the operation of the DC-DC converter, both to generate the output voltage as precisely as possible (e.g., to regulate it to a fixed or variable setpoint) and to optimize the energy efficiency of the DC-DC converter. In this context, particular consideration must be given to switching losses when the switch is operated under load, which can be advantageously minimized by a well-designed switching strategy (e.g., so-called quasi-resonant operation).

[0009] Against this background, there is, for example in the automotive sector, a great need for application-specific integrated circuits (ASICs) for use as control devices for DC-DC converters installed on board vehicles, with which a precise generation of the output voltage can be achieved for the respective converter topologies and thus specifically constructed and dimensioned converter circuits, while simultaneously ensuring high energy efficiency of the DC-DC converter.

[0010] One disadvantage of this state of the art, however, is that energy-efficient ASICs ("Soft Switching DC-DC Converter ICs") are relatively rare or comparatively expensive in the automotive sector. The high qualification requirements and often limited production volumes in this area must be considered. ASIC components that meet these requirements are therefore associated with high development and production costs. Long-term availability is further hampered by the rapid technological advancements in the semiconductor industry, the persistent need for shrinking, redesigning, and rationalization measures, and, not least, the increasing frequency of global semiconductor crises.

[0011] Another disadvantage of the well-known use of ASICs for controlling converter circuits is that greater flexibility in the control circuitry of DC-DC converters would be desirable to allow adaptation to wider power and voltage ranges of DC-DC converters. The currently available, common ASICs are not universally applicable, but only for very specific applications.

[0012] Especially in the automotive sector, a further disadvantage of the DC-DC converter concepts used in this area is that, to measure the current flowing through the switch, a shunt resistor arranged in series with the switch is used in conjunction with a voltage amplifier to amplify the measuring voltage drop across the shunt resistor, which represents a considerable effort and entails corresponding costs.

[0013] It is therefore an object of the present invention to provide a DC voltage converter that can be implemented cost-effectively and yet is flexibly adaptable to specific applications, particularly in the automotive sector.

[0014] The problem is solved by the features of the independent patent claims. Advantageous embodiments are characterized in the dependent claims.

[0015] According to the invention, this problem is solved by a

[0016] A DC-DC converter comprising an input for supplying an input voltage to the DC-DC converter, an output for outputting an output voltage of the DC-DC converter, and a converter circuit functionally arranged between the input and the output. The converter circuit includes a controllable switch designed as a semiconductor switch and an energy storage device that can be cyclically charged and discharged by alternately switching the switch on and off. Furthermore, the converter circuit includes a control device configured to monitor the input voltage, the output voltage, a voltage applied to the switch, and a current flowing through the switch during operation of the DC-DC converter in order to determine the switching-on and switching-off times based on the results of this monitoring and to control the switch accordingly.

[0017] The control unit of the DC-DC converter is implemented by a microcontroller module comprising a processor, a working and program memory module, and a peripheral device configurable by external circuitry of the microcontroller module and / or by software in the program memory and connected to the converter circuit, and that for monitoring the current flowing through the switch, a simulation of this current, realized by means of the microcontroller module and based on a mathematical model, is provided in order to determine this current taking into account the result of monitoring one or more of the aforementioned voltages.

[0018] The voltage monitoring provided by the invention can, in particular, include, for example, the continuous measurement of the respective voltage (especially, for example, the input voltage and / or output voltage). However, the monitoring of the voltage applied to the switch can also include, for example, the detection of the voltage exceeding and / or falling below at least a predetermined threshold value. Similarly, the result of monitoring the current flowing through the switch can, for example, represent a time-resolved profile of this current (determined by means of simulation). Alternatively or additionally, the result of this monitoring can also include, determined by simulation, the times at which this current exceeds and / or falls below at least a predetermined threshold value.

[0019] In a microcontroller component, such as that used within the scope of the invention and often also referred to as a single-chip computer system or system-on-a-chip (SoC), the processor (possibly comprising multiple processor cores), the working and program memory, and the peripheral components are typically interconnected via one or more internal digital bus systems. The peripheral components can comprise a variety of different peripheral modules to perform various peripheral functions, such as data input and output (interface function), analog-to-digital conversion (ADC), digital-to-analog conversion (DAC), comparators, driver outputs, etc. Within the scope of the invention, software configuration of the peripheral components in program memory can, for example, include programmatically writing to registers of the peripheral components during the initialization of the microcontroller component.

[0020] The invention allows the DC-DC converter to be implemented advantageously and particularly cost-effectively, at least in those cases where at least one microcontroller module is already provided in the relevant installation environment, such as in a vehicle. Such a microcontroller module can primarily serve other purposes (e.g., motor control, etc., as the so-called "main application"), but can also be used to implement a DC-DC converter according to the invention.

[0021] The invention allows the DC-DC converter to be flexibly adapted to new applications in a comparatively simple manner, thanks to the high variability of control tasks that can be handled by a microcontroller. For example, in the DC-DC converter for controlling a switch in the form of a FET, especially a MOSFET, there is greater flexibility in designing a specific gate driver characteristic. Furthermore, the use of the microcontroller component enables straightforward scalability with regard to the voltage and power dimensioning of the converter.

[0022] In one embodiment of the invention, the converter circuit is configured, for example, as a "boost converter" (see, for example, Fig. 3). Alternatively, a configuration as a "fly-back converter" or as a "sepic converter" is also possible.

[0023] Particularly with regard to the use of the DC-DC converter on board a vehicle, the DC-DC converter according to the invention can be advantageously designed, for example, for supplying an input voltage in the range of 5-30 V, particularly 10-20 V, and / or for outputting an output voltage regulated to a (e.g., fixed) setpoint of at least 24 V, particularly at least 48 V. On the other hand, achieving an output voltage of a maximum of 100 V is sufficient in many applications.

[0024] Regarding electrical power, the DC-DC converter can be designed, for example, for an achievable output power of at least 10 W, and in particular at least 50 W. On the other hand, it is often sufficient if this output power is, for example, a maximum of 150 W, and in particular a maximum of 100 W.

[0025] Furthermore, the invention advantageously adapts zero-crossing detection or zero-voltage detection (ZVD), which is used in many converter concepts to increase efficiency, to specific applications, for example, with regard to switching point search. Within the scope of the invention, special implementations of such switching point search, such as valley switching and / or valley skipping, can also expand the application range of the DC-DC converter. Zero-voltage detection (ZVD) or the associated switching point search can, for example, be provided in the DC-DC converter according to the invention for the voltage applied to the switch, in order to switch the switch during alternating switching operations at a voltage of zero (or at least approximately zero), or in a valley of the time course of this voltage, for example, to turn it on (e.g.,for quasi-resonant operation of the converter).

[0026] In many cases, the invention can also advantageously reduce the number of external components (implemented outside the microcontroller module), which can mean a significant cost advantage.

[0027] In this respect, it is essential that in the DC voltage converter according to the invention, the monitoring of the current flowing through the switch comprises a simulation of this current realized by means of the microcontroller module and based on a mathematical model, so that the use of a shunt resistor for measuring this current is unnecessary in the invention.

[0028] The elimination of the shunt resistor (as well as the downstream shunt voltage amplifier) ​​achievable with the invention, by replacing this conventional current measurement with a current simulation, represents a significant advantage in cost-sensitive applications. In known converter designs, a comparator with a variably adjustable threshold is typically used downstream of the shunt voltage amplifier to monitor the current flowing through the switch and determine the switch-off time based on this monitoring. While microcontroller chips often have such comparators in their peripherals, the use of current simulation within the scope of the invention eliminates the need for such a comparator, allowing it to be advantageously provided to the main application running on the microcontroller chip. The simulation provided for in the invention can be a so-called...The "Real Time Math Model" includes an indirect (mathematical) measurement of the current and / or the measurement of when the current exceeds or falls below a predefined threshold. The model underlying the simulation can, for example, consider not only the electrical properties of the converter circuit components (component parameters) and the current switching state of the switch, but also at least the output voltage (which can be measured, for example, by analog-to-digital conversion). Furthermore, the model can also take into account the input voltage, particularly if fluctuations in the input voltage cannot be ruled out in the specific application. If a so-called "soft start phase" is provided (e.g., to initiate quasi-resonant operation), the model can also account for the specific dynamics during the soft start phase.In the case of a control loop for regulating the output voltage to a specific setpoint (external control loop), the model can also take into account at least one quantity derived from the control loop.

[0029] By monitoring the current flowing through the switch and evaluating the results of a current simulation, it is possible, for example, to determine times when the current reaches an extreme value and / or times when the current reaches (exceeds or falls below) a predefined threshold. In a more specific embodiment for use with a quasi-resonant converter (e.g., a "boost converter"), an intra-cycle current peak (time and / or current intensity) is calculated during converter operation and used, for example, in connection with switching off the switch. Switching off can occur, for example, precisely at a simulated / calculated time of a current peak, or at a time offset from it. This time offset can be determined, for example, within a switching strategy, depending on the current operating state or current operating parameters (e.g.,The output voltage and / or input voltage can be calculated. By simulating a peak current, for example, a time to switch off the switch can be determined or a corresponding switch-off signal can be generated.

[0030] By using suitable filters in a control loop to regulate the output voltage to its setpoint, the invention advantageously ensures a control profile adapted to the specific application and / or operating situation, which is also suitable, for example, in the case of special or problematic operating situations (such as...).

[0031] input voltage fluctuations and / or output load fluctuations) ensure sufficient stability of the control system and meet the requirements regarding the stability of the output voltage.

[0032] The simulation of the current flowing through the switch can be achieved in various ways within the scope of the invention, in particular, ultimately (during operation of the converter circuit), for example, by processing signals defined by parameters of the switching strategy. These signals are derived from monitoring the input voltage, the output voltage, and the voltage applied to the switch. As explained further below, this signal processing, as well as the determination of the switch-on and switch-off times, can be performed using a channel sequencer of the microcontroller's peripheral device. The determination of the switch-on and switch-off times can employ appropriately modified signal processing to implement different operating modes (e.g., soft start phase, normal operating phase, etc.).

[0033] In conventional DC-DC converters with a shunt resistor for measuring the current flowing through the switch, the result of this measurement is often also used for an "overcurrent protection function" of the converter.

[0034] However, within the scope of the invention, monitoring of the converter operation, and in particular monitoring of the current in question, can also be advantageously carried out without such a shunt resistor to implement such an overcurrent protection function. For this purpose, in one embodiment, for example, the peripheral device of the microcontroller component may include a so-called IOM (Input Output Monitor) module, and this module may be used to monitor the control signal by which the switch is controlled (e.g., a quasi-resonant PWM signal). Using the IOM module, this signal can be monitored for compliance with certain criteria, and thus, for example, current limiting can be implemented. Furthermore, if an excessively high current is detected, for example, the converter may be forcibly shut down.

[0035] Alternatively or additionally to the implementation of an overcurrent protection function, the invention can also provide for monitoring the output voltage of the DC-DC converter to implement an overvoltage protection function using the microcontroller module or the peripheral device of the microcontroller module.

[0036] Common microcontroller components suitable for the invention often feature so-called "fast comparator" modules in their peripherals, but their number is typically very limited. In this respect, a further positive side effect of the monitoring of the current flowing through the switch by simulation, as provided in the invention (e.g., including the detection of threshold exceedances or falls below thresholds), is that no fast comparator module is required for this monitoring / detection (and, for example, for generating a switch-off signal from a peak current). Such fast comparator modules can then advantageously be made available to a main application running on the microcontroller.

[0037] This is particularly advantageous, for example, in applications of the converter with quasi-resonant "boost converter" or "flyback converter" concepts for DC-DC conversion on board a vehicle, where several step-up output voltages and, accordingly, several quasi-resonant control signals (e.g., PWM signals) are required. In one embodiment of the invention, several DC-DC converters of the type described herein are provided, in which the respective control devices are implemented by one and the same microcontroller module (or its correspondingly configured peripheral device).

[0038] For the voltage monitoring provided in the invention, corresponding connection points of the converter circuit can be connected directly or indirectly (e.g., via a voltage divider) to suitable connections (pins) of the microcontroller module. Any voltage supplied to the microcontroller module in this way can be monitored by means of the

[0039] A peripheral device (or its ADC module) can, for example, undergo analog-to-digital conversion for subsequent digital data processing. Alternatively or additionally, the peripheral device (or its ADC module) can be used for...

[0040] The comparator module of the same) can also be used to compare a voltage supplied in this way with a reference voltage.

[0041] In a preferred embodiment of the invention, the control device of the DC voltage converter is essentially implemented only by the peripheral device of the microcontroller module, which is configured appropriately for this purpose and connected to the converter circuit.

[0042] This is possible because modern microcontrollers often feature very powerful peripheral modules, which allow for the implementation of demanding control tasks without generating significant processor or system bus load. Processor and system resources can thus be advantageously allocated almost exclusively to one or more other tasks of the microcontroller (i.e., a "main application"). This is the case, for example, when the microcontroller's processor is only needed during initialization to configure the peripheral (e.g., by writing to the peripheral's registers), and the configured peripheral then autonomously performs the tasks of voltage detection and switching the DC-DC converter.

[0043] Within the scope of the invention, various peripheral blocks or peripheral modules of the microcontroller's peripheral device can be used, in particular, for example, one or more ADC modules and / or one or more comparator modules for the respective detection or comparison of one of the voltages to be monitored or, for example, detected in the invention, i.e., the input voltage, the output voltage, and the voltage applied to the switch.

[0044] Furthermore, a so-called GTM ("generic timer module") module of the microcontroller's peripherals can be used to generate a control signal for the switch as a result of signal processing. This control signal can be output by the microcontroller directly to a control pin of the switch (e.g., the gate of a FET), or to a driver circuit (e.g., a "gate driver"), which then generates a control voltage (e.g., gate voltage) to be applied to the switch's control pin. The signal and data processing performed in the microcontroller's peripherals, and thus the switching strategy for the DC-DC converter, can be advantageously defined by appropriate configuration of the peripherals.

[0045] For data processing, a device often referred to as a Multi-Channel Sequencer (MCS) can be used, as is often provided in the peripheral area of ​​modern microcontrollers (e.g. as a component of the aforementioned GTM module).

[0046] Implementing the control circuitry of the DC-DC converter primarily through the microcontroller's peripherals is therefore possible if the microcontroller has suitable peripheral modules such as ADC converters, comparators, GTM modules, etc. In modern microcontrollers, such modules are interconnected via configurable hardware interfaces, which advantageously enables particularly fast data processing without significant load on the system bus or processor. These configurable, networked peripheral blocks allow for the advantageous realization and improvement of, for example, semi-autonomous, encapsulated quasi-resonant boost converters with sophisticated switching strategies through real-time data processing. This eliminates the need for external ICs, such as ASICs dedicated to such DC-DC converters, and contributes to greater flexibility and optimization of the eBOM.Furthermore, microcontroller components of the aforementioned type are often suitable for the automotive sector.

[0047] In one embodiment, the peripheral device of the microcontroller component includes an ADC module, by means of which the input voltage and the output voltage are detected by applying these voltages or derived voltages, such as versions of these voltages divided by means of voltage dividers, to the inputs of the ADC module.

[0048] As already mentioned, the invention allows, for example, monitoring of the current flowing through the switch to implement an overcurrent protection function by means of a suitably configured IOM (Input Output Monitor) module of the peripheral device. This monitoring can, for instance, verify that the on-time (the duration in the cycle during which the switch is open) does not exceed a predefined threshold. The IOM module can be a standalone module of the peripheral device or, for example, an IOM module provided as a subcomponent of the aforementioned GTM module.

[0049] Alternatively or additionally to an overcurrent protection function, the invention also allows for monitoring of the output voltage to implement an overvoltage protection function using the microcontroller module or its peripherals. In one embodiment of the invention, one or more lookup tables (LUTs) are used in the control of the DC-DC converter circuit. These LUTs can be stored, for example, in a memory device of the microcontroller module's peripherals. Regarding the aforementioned overcurrent protection function using an IOM module, a LUT could, for example, be provided in a RAM module of the aforementioned GTM module (or its multi-channel sequencer (MCS)), from which a threshold (for the switch-on time) is read for a given operating state.

[0050] It is equally advantageous to provide at least one lookup table (LUT), e.g. stored in a RAM device of the peripheral device (e.g. the GTM module or the MCS), for determining the times for switching the switch on and off, from which at least one parameter of the switching strategy to be specified for a current operating state is read.

[0051] In one embodiment, the converter circuit includes a protection circuit configured to force the switch to turn off the converter circuit when at least one specific fault condition is met, indicating a particular fault (whether due to a fault in the converter circuit or the microcontroller). Such a protection circuit could, for example, be a driver circuit (e.g.,The protection circuit comprises a "gate driver" which receives an input signal from the peripheral device of the microcontroller chip and generates an output voltage applied to the control terminal of the switch. The protection circuit further includes an interference circuit section to which suitable signals for checking the fault condition criteria are supplied. If at least one fault condition criterion is met, this section modifies the input signal to the driver circuit in such a way that the driver circuit causes the switch to turn off. The protection circuit can, for example, be configured to force the switch to turn off if the converter's output voltage is excessively high. For this purpose, a signal representative of the output voltage (in particular, for example, the output voltage itself) can be supplied to the interference circuit section.

[0052] The protective circuit can also be designed, for example, to force the switch to shut off if an excessively high current flows through it. For this purpose, a signal representative of this current can be fed to the influencing circuit section.

[0053] The protection circuit can also be configured, for example, to force the switch to be turned off if any fault detected by the microcontroller occurs (including a failure of the microcontroller itself). For this purpose, at least one corresponding fault indication signal can be supplied to the influencing circuit section by the microcontroller.

[0054] However, within the scope of the invention, DC-DC converters can also be implemented in which the protection circuit described above requires fewer components or is omitted entirely (elimination of external components), provided the application in question allows for the implementation of the protection function without a "second instance" (external protection circuit) alongside a protection function implemented solely by the microcontroller. In this case, for example, the overcurrent protection circuit can be implemented by monitoring the control signal (e.g., PWM signal) output by the microcontroller via an IOM (Input Output Monitor) module or a channel of such a module.

[0055] In one embodiment, the peripheral device of the microcontroller chip includes a comparator module. This module monitors the voltage applied to the switch by applying this voltage, or a voltage divided by a voltage divider, to one input. Another input of the comparator module can be supplied with a (fixed or variable) predefined reference voltage. This allows for the detection of voltage exceeding or falling below certain threshold values.

[0056] In an alternative and particularly advantageous embodiment, the monitoring of the voltage applied to the switch is achieved by applying this voltage, or a version of this voltage divided by a voltage divider, to a Schmitt trigger input of the peripheral device.

[0057] This also allows for the detection of exceedances and / or falls below certain threshold values ​​due to this voltage. Besides EMC improvement, the main advantage of quasi-resonant converter operation lies in minimizing switching losses in the switch (e.g., MOSFET) by switching on without a significant voltage applied to the switch. Therefore, the precise determination of the optimal switching point according to the ZVD concept within the switching strategy is essential for efficient converter operation. While a "ZVD signal" defined by the voltage applied to the switch or its temporal profile can be read, for example, via a "Fast Comparator" module in the peripherals and connected to a corresponding MCS channel via a dedicated hardware interface in a system-friendly manner, if the ZVD is triggered via a Schmitt trigger input (e.g., a so-called...)Implementing the "General Purpose I / O Pin" offers the particular advantage of making more comparator modules available for the main application of the microcontroller chip. It should be noted that, unlike comparator modules, Schmitt trigger inputs are usually readily available in the peripherals of common microcontrollers. Furthermore, this embodiment, for example, when configuring a suitable hardware interface to the MCS, avoids system bus load due to the control of the converter operation. The optimal switch-on time can be achieved, for example, by an adjustable delay (from the switching point of the Schmitt trigger). In one embodiment, the switching-on and switching-off times of the switch (according to the switching strategy) are determined in such a way as to achieve quasi-resonant operation of the DC-DC converter.

[0058] According to another aspect of the invention, the use of a DC-DC converter of the type described herein, or several such DC-DC converters, for DC-DC conversion on board a vehicle is proposed.

[0059] In this application, the microcontroller module can advantageously also perform at least one other control task for the vehicle ("main application" of the microcontroller), e.g., to control an engine (e.g., internal combustion engine or electric motor) on board the vehicle, or e.g., to control components of such an engine, such as a fuel injection system of an internal combustion engine or an inverter of an electric drive motor on board the vehicle.

[0060] Another interesting control task or main application of the microcontroller within the scope of the invention is the control of a (further, different) DC-DC converter, which is provided on board the vehicle for conversion, in particular bidirectional conversion, between a first voltage greater than 400V, in particular greater than 600V, and a second voltage less than 50V, in particular less than 25V (e.g.

[0061] DC-DC converter between the low-voltage electrical system (e.g., 12V) and the high-voltage electrical system (e.g., approx. 800V) of an electrically powered vehicle (e.g., HEV, BEV). In this case, the output voltage of the DC-DC converter according to the invention (e.g., in the range of approximately 20-60V) can advantageously serve as an "auxiliary voltage" for supplying a driver circuit for controlling one or more power semiconductor switches (e.g.,

[0062] SiC FETs) in the (other) DC-DC converter. Another possible control task or main application of the microcontroller on board a vehicle is the control of a so-called "on-board charger" device for converting an AC voltage supplied to the vehicle, e.g., via a charging station, into a DC voltage suitable for charging an electrical energy storage device (battery).

[0063] One or more of these other control tasks can be performed by a main application running on the microcontroller chip, whereby it may be provided that a large portion, in particular almost exclusively, of the processor and system performance of the microcontroller chip is made available for the main application.

[0064] When using a DC-DC converter according to the invention on board a vehicle, it may be provided, for example, that a vehicle electrical system voltage in the range of 5-30 V is supplied as the input voltage. In the case of step-up conversion, the output voltage may, for example, be regulated to a setpoint in the range of 20-100 V.

[0065] A preferred use of an output voltage provided on board a vehicle by means of a DC-DC converter (e.g., step-up) is to power a driver circuit for controlling power semiconductor switches (e.g., MOSFETs, SiC-FETs, etc.) in a power electronic device such as an inverter for supplying power to the vehicle's electric drive motor (e.g., BEV or HEV), or, for example, to power a driver circuit for another DC-DC converter. Furthermore, such an output voltage can be used on board a vehicle as a supply or control voltage for an actuator (e.g., magnetic actuator, piezo actuator, etc.), for example, in a valve assembly (e.g., in a fuel injection system for an internal combustion engine).

[0066] According to another aspect of the invention, a computer program product comprising program code, executed on a microcontroller chip, performs a method for controlling the converter circuit of a converter of the type described herein or a suitable configuration of a peripheral device of the microcontroller chip for this purpose.

[0067] The invention is further described below with reference to exemplary embodiments and the accompanying drawings. These depict:

[0068] Fig. 1 shows a DC / DC converter according to an embodiment of the prior art,

[0069] Fig. 2 shows a DC / DC converter according to an embodiment of the invention,

[0070] Fig. 3 shows an embodiment of a converter circuit that can be used in the DC-DC converter of Fig. 2.

[0071] Figs. 4 to 7 show exemplary embodiments of circuit components that can optionally be used in the converter circuit of Fig. 3, namely voltage dividers (Figs. 4 to 6) and a protection circuit component (Fig. 7).

[0072] Fig. 8 shows an exemplary time course representation of a current flowing through a switch used in the converter circuit of Fig. 3, and of a voltage applied to this switch, and

[0073] Fig. 9 shows an exemplary time course representation of a control voltage applied to the switch, a current flowing through a choke used in the converter circuit of Fig. 3, and the voltage applied to the switch.

[0074] Fig. 1 shows an embodiment of a DC-DC converter 1 in a configuration known from the prior art. The converter 1 comprises an input 10 for supplying an input voltage VBR, an output 20 for outputting an output voltage Vboost, and a converter circuit 30 functionally arranged between input 10 and output 20. The converter circuit 30, supplied with the input voltage VBR on the input side, generates the output voltage Vboost on the output side, which in the illustrated example (a "boost converter" topology) is higher than the input voltage VBR (boost conversion, i.e., Vboost > VBR).

[0075] Input 10 has a first (positive) terminal, as shown at the top of Fig. 1. A second (negative) terminal of input 10 is formed by a ground terminal (GND). Output 20 has a first (positive) terminal, as shown at the top of Fig. 1, with a second (negative) terminal of output 20 being formed by the ground terminal (GND). In the converter design shown, there is therefore galvanic coupling between input 10 and output 20. The voltages VBR and Vboost are referenced to a common ground potential (GND). In contrast to this example, modified designs could also provide galvanic isolation between the input and output voltages (in particular, for example, with a converter circuit designed as a "flyback converter" or as a (modified) "sepic converter").

[0076] To accomplish the voltage conversion from VBR to Vboost, the converter circuit 30 includes a controllable semiconductor switch T1 (here: MOSFET) and an energy storage device (DC link energy storage device) in the form of an inductor L1, which can be cyclically charged and discharged by alternately switching this switch T1 on and off. In the illustrated example, a capacitor Ores is connected in series with the inductor L1 and in parallel with the switch T1.

[0077] Furthermore, the converter 1 includes a control unit 40 in the form of an application-specific integrated circuit (ASIC) which continuously monitors the voltages VBR and Vboost, a voltage Vzvd applied to switch T1, and a current Ids flowing through switch T1 during the operation of the converter 1 in order to determine specific times for switching on and off the switch T1, taking into account the result of this monitoring, and to control the switch T1 accordingly by means of a control voltage Gdrive.

[0078] To measure the current Ids, a shunt resistor Rshunt is arranged in series with the switch T1, whereby a measuring voltage (measuring potentials CSP, CSN) dropping across the shunt resistor Rshunt is supplied to the control device 40, which represents a measure of the current Ids.

[0079] The control unit 40 implements a "switching strategy" when controlling switch T1, largely determined by the internal structure of the ASIC. According to this strategy, switching switch T1 on and off depends on the results of continuous measurements of VBR, Vboost, Vzvd, and Ids. This strategy essentially represents an algorithm for determining the times for switching switch T1 on and off, ensuring that Vboost in the illustrated example is regulated to a fixed setpoint and that switching losses during the switching of switch T1 are minimized by implementing quasi-resonant operation.

[0080] The basic structure of the converter circuit 30 ("boost converter" topology) is described as follows: The converter circuit 30 comprises

[0081] - a first line path leading from the first (positive) input terminal of input 10 to a circuit node K, in the course of which the choke L1 is arranged (In the example shown, an input-side filter 11 is also (optionally) provided in the course of the first line path to reduce interference),

[0082] - a second conductor path leading from circuit node K to the first (positive) output terminal of output 20, in the course of which a diode D1 is arranged as shown, - a capacitor Cout arranged at output 20, between the output terminals of output 20 for buffering or smoothing the output voltage Vboost, and

[0083] - a third conductor path, which leads from the circuit node K to the common reference potential GND (or thus to the second terminals of input 10 and output 20) and in the course of which the switch T1 and the shunt resistor Rshunt are arranged in series with it.

[0084] In the example shown, the converter circuit 30 also includes the capacitor Ores, arranged in parallel to the switch T1, on the third line path (for the purpose of realizing quasi-resonant converter operation).

[0085] Furthermore, the converter circuit 30 comprises a first voltage divider DIV1 for supplying a split version of the input voltage VBR to a SHUTDOWN terminal of the control unit 40, a second voltage divider DIV2 for supplying a split version of the output voltage Vboost to terminals EampO and EampN of the control unit 40, and a detection path Pzvd for supplying a detection signal to a terminal ZVD of the control unit 40 for monitoring the voltage (DC link voltage) Vzvd applied to switch T1. The detection path Pzvd shown in the example (with a series connection of resistor and capacitor) is designed for detecting the (descending) edge of the voltage Vzvd.

[0086] The basic operating principle of converter 1 can be described as follows: When converter 1 is switched off, switch T1 is permanently open. The input voltage VBR is then also present at node K via the first circuit path (and the capacitor Cres is charged to the voltage VBR). The diode D1, located in the second circuit path, (always) prevents current flow in the "wrong" direction, i.e., from the first output terminal to node K. During operation of converter 1, switch T1 is alternately switched on and off by means of the PWM control voltage Gdrive supplied to the control terminal (gate) of switch T1. When switch T1 is switched on, node K is connected to ground potential GND, and consequently, a current Id, which increases over time, flows through the inductor L1.When switch T1 is then switched off, the voltage Vzvd at node K rises sharply (due to the induction in the inductor L1), and the capacitor Cres is increasingly charged. As soon as the voltage Vzvd reaches the value of the output voltage Vboost, a current at this voltage level Vboost begins to flow from node K via diode D1 to the output terminal. However, due to the (energy) discharge of the inductor L1, this current flow ceases, and the voltage Vzvd drops again. These processes then repeat cyclically. The output voltage Vboost is buffered by the capacitor Cout. To regulate Vboost stably to, for example, a fixed setpoint, the switching-on and switching-off times must be appropriately determined. The later the switching occurs, according to a "switching strategy," for example...The closer the switch-off point is chosen to the rise of the inductor current Id, the greater the subsequent energy transfer to the output 20 of converter 1 in the respective cycle (where an increased / decreased energy transfer tends to increase / decrease the output voltage Vboost). In the illustrated example, the capacitor Cres, in combination with the inductor L1, forms a resonant circuit, which makes it possible, in so-called quasi-resonant operation, to select the switch-on points such that the voltage Vzvd applied to switch T1 is at least approximately zero when it is switched on, in order to minimize switch-on losses.

[0087] Disadvantages include the comparatively high cost of ASICs (control unit 40) optimized for energy efficiency in converter operation, as well as high development costs, for example, with regard to approval / qualification required in the automotive sector (e.g., AEC-Q100). Furthermore, such commercially available ASICs are only suitable for a more or less specifically defined application. In addition, the "shunt resistor" concept used to measure the current Ids incurs considerable costs. The invention enables the cost-effective realization of DC-DC converters that can be flexibly adapted to specific applications. In the following description of further embodiments, the same reference numerals are used for components with the same operating characteristics. The focus is essentially only on the differences compared to the aforementioned invention.The embodiments already described have been addressed, and reference is expressly made hereto to the description of previous embodiments.

[0088] Fig. 2 shows an embodiment of a DC voltage converter 1 according to the invention, which, like the converter already described with reference to Fig. 1, has an input 10 for supplying an input voltage VBR, an output 20 for outputting an output voltage Vboost, a converter circuit 30 arranged functionally between them and a control device 40.

[0089] Fig. 3 shows an embodiment of a converter circuit 30 that can be used in the DC-DC converter 1 of Fig. 2. As in the example of Fig. 1, this circuit has a controllable switch T1 (here: MOSFET) with a parallel-connected capacitor Ores, as well as an energy storage device in the form of an inductor L1 that can be cyclically charged and discharged by alternately switching the switch T1 on and off. As in the example of Fig. 1, this is a "boost converter" topology for step-up conversion (Vboost > VBR). The basic structure of the converter circuit 30 (Fig. 3) and the basic operating principle of the converter 1 (Fig. 2) are the same as described above for the example of Fig. 1 (with first, second, and third transmission paths). However, a significant difference lies in the design of the control device 40 and the omission of the shunt resistor (Rshunt) required in the example of Fig. 1.

[0090] Returning to Fig. 2, the control device 40 is designed, as in the example of Fig. 1, to continuously monitor the input voltage VBR, the output voltage Vboost, a voltage Vzvd applied to switch T1, and a current Ids flowing through switch T1 during the operation of the converter 1, in order to determine the times for switching on and off of switch T1 according to a predetermined switching strategy, taking into account the result of this monitoring, and to control switch T1 accordingly.

[0091] However, an advantageous feature of the converter 1 of Fig. 2 is that the control device 40 is implemented by a microcontroller module comprising a processor unit 41, a working and program memory unit 42 and a peripheral device 43 which can be configured by external circuitry of the microcontroller module and / or by software in the program memory and which is connected to the converter circuit 30, and that for monitoring the current Ids flowing through the switch T1 a simulation of this current Ids is provided by means of the microcontroller module and based on a mathematical model in order to determine this current Ids taking into account the result of the monitoring of the voltages VBR, Vboost, Vzvd.

[0092] In this respect, an advantageous feature of the converter circuit 30 of Fig. 3 is that no shunt resistor is provided in this circuit 30 for current measurement.

[0093] Figures 4 to 6 show exemplary voltage dividers DIV1, DIV2, and DIV3, which can be used in the converter circuit 30 of Figure 3 to obtain voltage-divided versions of the voltages VBR, Vboost, and Vzvd tapped at suitable points (VBRmeas, Vboostmeas, Vzvdmeas) of the converter circuit 30. These divided versions are fed to the respective inputs ANvbr, ANvboost, and COMPzvd of the microcontroller module 40 to be detected and evaluated within the switching strategy.

[0094] Using a model-based simulation of the current Ids, the time intended for switching off the switch (see T1 in Fig. 3) is no longer determined by a shunt current measurement in the primary circuit, as in the prior art. Instead, in the example shown, an "on time" and thus the aforementioned switch-off time is determined (calculated) in real time by a so-called channel sequencer (subcomponent of a GTM module in the periphery 43), whereby a corresponding value can also be read from a LUT (lookup table).The starting point is a mathematical model of the circuit concept, in this example the converter circuit 30, in which one or more, in particular all, acquired measured variables (VBR, Vboost, Vzvd, and / or dependent signals such as a "ZVD signal"), an instantaneous switching frequency and / or an instantaneous duty cycle of a switch control signal, as well as the component parameters used in the specific converter circuit (and tolerances if applicable) can be taken into account.

[0095] Particularly advantageous in the model, and for the switch control based on it (see T1 in Fig. 3), is the ability to consider variations depending on the current operating state (e.g., for different load situations). With simulation support, lookup tables (LUTs) for several different operating modes of the converter can be generated during the design phase. From these LUTs, corresponding control parameters (especially regarding switch control times) can be read out, depending on the input and output voltages. These control parameters can then be taken over and applied, for example, by a so-called channel sequencer of an MCS module located in the periphery 43. The aforementioned operating modes can include, for example, a "soft start" mode, a "normal" mode, and / or a "burst" mode.

[0096] In soft start mode (with hard switching), for example, a PWM control signal starts with a short "on time," and this on time is gradually increased using the channel sequencer. The parameters determined during the design process are stored, for example, in a LUT (Load Use Table). In this way, the duration of the soft start mode and the steepness of the on-time increase can be defined as a function of the input voltage VBR and, if applicable, Vboost (output-side load situation), and used to control the converter circuit. In a more refined version, the switching frequency of the PWM signal can also be adjusted during the soft start mode, in addition to the duty cycle.

[0097] The normal mode (with soft switching, quasi-resonant phase) can be activated after a specific soft start period, which is long enough to detect zero crossings in the voltage Vzvd. In normal mode, the switch-on times can now be determined with optimized power loss (quasi-resonant converter operation). For example, in normal mode, the duty cycle for the next switching cycle (switch on / off) can be derived directly (without system bus load) from the output voltage monitoring or acquisition via the hardware interface and fed into the channel sequencer. In one embodiment, the last duty cycle is maintained within a predefined tolerance band, and if the tolerance band is exceeded or fallen below, the duty cycle is increased or decreased, for example, by a predefined value (increment or decrement).

[0098] Furthermore, a dynamic control mechanism can be implemented in which the aforementioned increment and / or decrement is specified, for example, depending on the magnitude of the output voltage change. A corresponding parameterization can also be defined during the design phase and stored in a LUT for normal mode during converter operation. This LUT can then be read in real time by the channel sequencer and advantageously taken into account when determining the switching times.

[0099] Taking into account an input voltage (VBR) read into the channel sequencer via a hardware interface allows for a fast response in the next cycle, even to changes in the input voltage. A corresponding parameter can also be stored in a LUT for normal mode and thus advantageously considered for converter operation. Burst mode can be used, for example, in the case of a significantly decreasing output load. In this case, the switch's turn-on time is reduced in normal mode, and the switching frequency can increase up to a design-defined maximum. The output voltage Vboost would then exceed its target value. To prevent this, the quasi-resonant normal mode can be exited, and in burst mode (with hard switching or, for example, "valley switching"), the lightly loaded output voltage can be maintained effectively with significantly reduced turn-on bursts.One simple implementation involves providing individual PWM pulse groups to control the switch, interrupting longer off-times.

[0100] The input voltage VBR and the output voltage Vboost are detected in the example using respective ADC modules of the peripheral device 43, whereas for monitoring the voltage Vzvd, a comparator module (especially a "Fast Comparator" module) of the peripheral device 43 of the microcontroller chip 40 could also be used, for example, to monitor the voltage Vzvd for reaching one or more threshold values ​​and to take the result of the monitoring into account in the switching strategy.

[0101] In the illustrated embodiment, monitoring of the voltage Vzvd is achieved by applying a so-called Schmitt trigger input of the peripheral device 43 with the version COMPzvd of the voltage Vzvd, divided by the voltage divider DIV3 (Fig. 6). This input can, for example, be a pin of a so-called port module of the peripheral device 43 (such pins are conventionally used for inputting digital signals, with the Schmitt trigger handling the signal decoding to levels "0" and "1"). While the switching threshold of the Schmitt trigger is practically fixed by the given technology (e.g., CMOS), the desired switching threshold for the voltage Vzvd can be defined by appropriately designing the voltage divider DIV3 (resistance values). During operation of the converter circuit 30 (Fig.3) A variably adjustable optimal switch-on time for the switch T 1 can be achieved by an adjustable time delay between the switching time of the Schmitt trigger and the output of a corresponding control signal (see "UCgdrive" in Fig. 2 and 7).

[0102] Fig. 7 shows an exemplary protection circuit 50, which, in the event of certain fault conditions, causes the switch T1 (Fig. 3) to be forcibly switched off. The illustrated protection circuit 50 comprises a driver circuit 51 (gate driver), which receives a control signal UCgdrive output by the peripheral device 43 of the microcontroller module 40 and outputs the control voltage Gdrive to be applied to the control terminal (gate) of the switch T1. Furthermore, the protection circuit 50 comprises an interference circuit section 52, to which, in this example, the output voltage Vboost and various signals (here: GD_RESET_VPOWER_0V, GD_RESET_ERROR, uC_RESET) are supplied, each of which signals the presence (or absence) of a specific fault condition and which are linked or connected in the protection circuit 50 as shown.The system processes a fault signal F output by the influencing circuit section 52, which can be used to force the switch T1 to be switched off. In this example, the signal F acts directly on an input of the driver circuit 51, as shown in Fig. 7. Thus, if at least one of several fault criteria is met, which is determined by the protection circuit 50 based on the supplied signals, the switch T1 is switched off and the converter 1 is therefore taken out of service.

[0103] In the example, the protection circuit 50 causes such a shutdown of the converter 1 both in the presence of an excessively high output voltage Vboost and in the presence of any fault case detected by the microcontroller.

[0104] To ensure that the converter 1 is shut down by switch T1 even in the event of an excessively high current Ids, the illustrated protection circuit 50 could be modified from the example shown in Fig. 7, for example, to additionally obtain and consider a signal representative of this current Ids (or a corresponding fault indication signal). In the illustrated example, to implement such an overcurrent protection function with respect to the current Ids, the control signal UCgdrive output during converter operation is monitored by means of an IOM (Input Output Monitor) module of the peripheral device 43 of the microcontroller chip 40. By appropriately configuring the IOM module, an anomaly in the UCgdrive signal can be detected in order to take appropriate protective measures. For this purpose, for example, a corresponding fault indication signal from a (modified) protection circuit of the aforementioned type could be taken into account.

[0105] Fig. 8 shows exemplary waveforms of the current Ids and the voltage Vzvd over time t during the operation of the converter circuit 30 of Fig. 3, specifically in a phase at the end of the discharge of the inductor L1 or at the end of a PWM cycle of the control of the switch T1, in which the current Ids and the voltage Vzvd initially drop sharply and then oscillate towards their respective equilibrium values ​​(Ids -> 0; Vzvd -> VBR). The dynamics shown, including the phase shift between the time waveforms of Ids and Vzvd, result essentially from the electrical properties of the converter circuit 30 or the resonant circuit formed by the capacitor Cres and the inductor L1 (which, within the scope of the invention, also allows the current Ids to be mathematically modeled or simulated).

[0106] In the time phase shown in Fig. 8, a point for switching on switch T1 (to initiate the next PWM cycle) is to be determined by means of the microcontroller module 40 or the suitably configured peripheral device 43 according to the switching strategy defined therein. The aim here is to minimize switching losses in switch T1 (quasi-resonant PWM control, for example in a "normal mode" of the type explained above). Therefore, favorable times "ton" for switching on are generally found in a valley in the time course of the voltage Vzvd ("valley switching"), in the example of Fig. 8, for instance, in the region marked by a double arrow in which the voltage Vds has the value zero (see the exemplary time "ton").

[0107] Within the scope of the invention, the determination of the time for switching on the switch can thus advantageously be based on a zero-crossing detection or zero-voltage detection ("zero voltage detection", ZVD) with respect to the voltage Vzvd (or more generally a valley or minimum detection with respect to this voltage).

[0108] In a particularly advantageous embodiment within the scope of the present example, as well as generally within the scope of the invention, such a central voltage distribution (CVD) is implemented via a Schmitt trigger input of the peripheral device 43 of the microcontroller module 40. In this example, the voltage Vzvd is detected via this Schmitt trigger input of the peripheral device 43 by applying the version of the voltage Vzvd divided by the voltage divider DIV3 (see Fig. 3, 6). Common microcontroller modules typically have sufficient Schmitt trigger modules or inputs. In particular, a pin of a so-called port module of the peripheral device 43 can be used (which is conventionally also usable for inputting digital signals).

[0109] The time for switching on switch T1 can be chosen, for example, as the switching point of the Schmitt trigger (in the case of a suitable switching threshold of the Schmitt trigger).

[0110] In a particularly advantageous embodiment of the invention, an optimal switching time, starting from the Schmitt trigger's switching point, is achieved by an adjustable time delay. This adaptable ZVD switching point search advantageously allows for additional flexibility of the DC-DC converter according to the invention with regard to further voltage and power classes and / or the use of other converter components. The invention also advantageously allows, for example, the implementation of special PWM control modes for low-load applications (e.g., "valley-skipping mode"), as well as optimized burst modes for switching frequency regulation. This will be explained below with reference to Fig. 9.

[0111] Fig. 9 shows exemplary curves of the control voltage Gdrive, the choke current Id and the voltage Vzvd over time t.

[0112] The diagram in Fig. 9 illustrates a control mode in which, in each control cycle, the time "ton" for switching on switch T1 is set after a first valley in the voltage Vzvd time series, i.e., (at least) one valley is "skipped" ("valley-skipping mode"). In the example in Fig. 9, only the first valley is skipped, and this time "ton" is set in the region of a second valley in the voltage Vzvd time series. In contrast to this example, with such a control mode it is also possible to skip more than one valley before switching on switch T1. This reduces the switching frequency resulting in converter operation.

[0113] In one embodiment, the switching strategy provides for the control mode ("Valley-Skipping Mode") described above for a low-load range of converter operation.

[0114] In summary, the invention and the described embodiments enable the provision of a cost-effectively realizable yet flexibly adaptable DC / DC converter, particularly in the automotive sector, with an advantageous quasi-resonant operating mode. Reference numerals

[0115] 1 DC-DC converter GND Ground potential (reference potential) 10 Input VBR Input voltage 11 Input filter L1 Inductor (energy storage) Id Current through inductor (charging / discharging current) Rshunt Shunt resistor T1 Switch Vzvd Voltage at switch (DC link voltage) Pzvd Detection path Ids Current through switch UCgdrive Control signal Gdrive Control voltage t Time ton Time for switch-on toff Time for switch-off Ores Capacitor (resonant capacitor) K Circuit node D1 Diode Cout Output capacitor 20 Output Vboost Output voltage 30 Converter circuit DIV1 Voltage divider (for VBR) DIV2 Voltage divider (for Vboost) DIV3 Voltage divider (for Vzvd) 40 Control unit 41 Processor unit 42 Working and program memory unit 43 Peripheral unit 50 Protection circuit 51 Driver circuit 52 Interference circuit section F Fault signal

Claims

Patent claims 1. DC-DC converter (1) comprising an input (10) for supplying an input voltage (VBR) to the DC-DC converter (1), an output (20) for outputting an output voltage (Vboost) of the DC-DC converter (1), and a converter circuit (30) functionally arranged between the input (10) and the output (20), with a controllable switch (T1) designed as a semiconductor switch and an energy storage device (L1) that can be cyclically charged and discharged by alternately switching on and off the switch (T1), and further comprising a control device (40) configured to continuously monitor the input voltage (VBR), the output voltage (Vboost), a voltage (Vzvd) applied to the switch (T1), and a current (Ids) flowing through the switch (T1) during operation of the DC-DC converter (1), in order to determine the times (ton,to determine the switching on and off of the switch (T1) and to control the switch (T1) accordingly, wherein, - the control device (40) is implemented by a microcontroller module comprising a processor module (41), a working and program memory module (42) and a peripheral device (43) that can be configured by external circuitry of the microcontroller module and / or by software in the program memory and is connected to the converter circuit (30), and - for monitoring the current (Ids) flowing through the switch (T1), a simulation of this current (Ids) is provided by means of the microcontroller module and based on a mathematical model in order to determine this current (Ids) taking into account the result of monitoring one or more of the aforementioned voltages (VBR, Vboost, Vzvd).

2. DC voltage converter (1 ) according to claim 1, wherein the control device (40) is implemented essentially only by the peripheral device (43) of the microcontroller module which is configured appropriately for this purpose and connected to the converter circuit (30).

3. DC-DC converter (1) according to one of the preceding claims, wherein the peripheral device (43) of the microcontroller component comprises an ADC module by means of which the input voltage (VBR) and the output voltage (Vboost) are detected by applying these voltages (VBR, Vboost) to inputs of the ADC module or to versions of these voltages (VBR, Vboost) divided by means of voltage dividers (DIV1, DIV2).

4. DC voltage converter (1 ) according to one of the preceding claims, wherein the peripheral device (43) of the microcontroller component comprises a Schmitt trigger input and the monitoring of the voltage (Vzvd) applied to the switch (T1 ) is realized by applying this voltage (Vzvd) or a version of this voltage (Vzvd) divided by means of a voltage divider (DIV3) to this input.

5. DC-DC converter (1) according to any one of the preceding claims, wherein the determination of the times (ton, toff) for switching on and off of the switch (T1) is provided such that quasi-resonant operation of the DC-DC converter (1) is achieved.

6. Use of a DC-DC converter (1) according to any one of the preceding claims for DC-DC conversion on board a vehicle.

6. Computer program product comprising a program code executed on a microcontroller chip (40) comprising a processor device (41), a working and program memory device (42) and a peripheral device (43) configurable by external circuitry of the microcontroller chip and / or by software in the program memory and connected to a converter circuit (30), performing a method for controlling the converter circuit (30) or a configuration of the peripheral device (43) suitable for carrying out the method, such that a DC voltage converter (1 ) according to one of claims 1 to 5 is realized.

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