Methods and devices for phase synchronization of multiplex signal

Abstract

Methods and devices for the phase synchronization of a multiplex signal which are designed for: receiving a Pilot radio signal and a Data radio signal; generating in-phase and quadrature components of said signals; generating a Phase Detector (PD) signal for the Data radio signal using the in-phase component and quadrature component of the Data radio signal; generating a PD signal for the Pilot radio signal using the in-phase component and quadrature component of the Pilot radio signal; closing a feedback loop through a chain of units consisting of a loop filter, an NCO and correlators; generating a signal to reverse the polarity of the PD signal for the Data radio signal using the in-phase component of the Pilot radio signal; generating a corrected PD signal for the Data radio signal by multiplying the polarity reversal signal by the PD signal for the Data radio signal; generating an Extended Phase Detector (EDP) signal by weighted summing of the corrected PD signal for the Data radio signal and the PD signal for the Pilot radio signal to close the feedback loop.

Description

[0001] Methods and devices for phase synchronization of a multiplex signal

[0002] Field of technology

[0003] The invention relates to the field of processing signals from global navigation satellite systems (GNSS), such as GPS, GLONASS, Beidou, Galileo, etc., and can be used in GNSS receivers.

[0004] State of the art

[0005] Many GNSS satellites emit two radio signals on the same frequency: Data and Pilot. The Data signal has an inverse modulation of the carrier with a priori unknown binary symbols μ. b = ±1 (BPSK). At the same time, the Pilot signal does not have an inverse modulation of the carrier with a priori unknown binary symbols, but it may or may not have an inverse modulation of the carrier with the so-called secondary code, i.e. with a priori known binary symbols μ b = ±1.

[0006] To demodulate the binary symbols of a Data radio signal, sometimes only the Data radio signal is processed, leaving the Pilot radio signal unprocessed. This is done using a well-known phase-locked loop (PLL) circuit based on the Data radio signal. This approach is referred to below as Option 1, and the PLL circuit used is referred to as PLL. b (b - binary). In the FAP b Typically, a phase detector (PD) with a narrow arctangent (arctg) is used.

[0007] In option No. 1, the so-called “reverse operation” is possible, in which the transmitted binary symbol μ is erroneously estimated. b .

[0008] The reverse work occurs with a probability of 50% during the initial and repeated (after prolonged shading) entry of the FAP bin synchronization. The reverse operation is accompanied by so-called half-cycle shifts in the measurement of the carrier's full phase. Moreover, the possible full phase values ​​supplied by the receiver as part of the raw data can be shifted from each other by a multiple of half a cycle. These half-cycle shifts create additional complications for integer-valued phase ambiguity resolution in precise positioning (in RTK and PPP).

[0009] In the presence of two radio signals (Pilot and Data) simultaneously, one of the technical solutions is the following: to make an independent (autonomous) FAPρ for the Pilot signal, and filtered using the FAP р carrier used for coherent demodulation of binary information μ b in the Data radio signal. This method is referred to below as option #2. In phase-adjusted frequency converters (FACs), phase-adjusted frequency converters (PDs) with a wide arctangent (Arctg) are typically used.

[0010] Option #2 is preferable to option #1 for the following reasons:

[0011] • FAPr has a threshold SNR value that is several decibels better (lower) than FAP b (with the same powers of Pilot and Data radio signals and with the same FAP bands р and FAP b );

[0012] • in option No. 2 there is no reverse work and half-cycle shifts of the full phase.

[0013] However, in the linear mode (at high SNR), the standard deviation of the tracking errors in the FAPr and in the FAP b are the same (with the same PLL bands and with the same powers of the Pilot and Data radio signals), and therefore the standard deviation of the noise errors in measuring the full phase is also the same.

[0014] Analogues and prototypes

[0015] A signal processing method according to US Patent No. 10,797,836, hereinafter referred to as Variant No. 3, is a prototype for the present invention. Variant No. 3 simultaneously uses both components of the incoming multiplex radio signal (i.e., both the Data and Pilot radio signals) to synchronize the phase of the multiplex radio signal. This is in contrast to Variant No. 1, which uses only the Data radio signal to synchronize the phase of the multiplex radio signal, and to Variant No. 2, which uses only the Pilot radio signal to synchronize the phase of the multiplex radio signal.

[0016] The technical solution proposed in option No. 3 is based on the formation of a “coherent sum signal” containing the sum:

[0017] • demodulated Pilot radio signal; and

[0018] • the product of the demodulated Data radio signal and the feedback signal.

[0019] The specified sum is formed in block 268 of the prototype device. The input of block 268 receives two complex signals, designated in the prototype as "PR" and "P2," and their sum is designated "CS."

[0020] The claimed invention uses a different principle of joint processing of Data and Pilot radio signals.

[0021] The prototype talks about a multiplier and an inverse multiplier.

[0022] They may or may not be present in the present invention, but they are not relevant to the essence of the present invention, and therefore they are not discussed further.

[0023] The claimed invention, like the prototype, considers the processing of a Pilot radio signal both with and without a secondary code.

[0024] The disadvantage of known solutions is the complexity of implementation.

[0025] The purpose of the claimed invention is to eliminate the shortcomings of known solutions. The essence of the invention

[0026] The objective of the claimed invention is achieved through the use of an extended phase detector (EPD) circuit.

[0027] The first claimed method of phase synchronization of a multiplex signal includes:

[0028] - reception of the Pilot radio signal and the Data radio signal, including the formation of in-phase and quadrature components of these signals;

[0029] - formation of the Phase Detector (PD) signal of the Data radio signal using the in-phase and quadrature components of the Data radio signal;

[0030] - formation of the FD Pilot radio signal using the in-phase and quadrature components of the Pilot radio signal;

[0031] - closing the feedback loop through a chain of blocks consisting of a loop filter, NCO and correlators that generate in-phase and quadrature components of the Data radio signal and the Pilot radio signal; and is distinguished by the fact that it includes:

[0032] - formation of a signal for changing the polarity of the FD Data radio signal using the in-phase component of the Pilot radio signal;

[0033] - formation of a corrected FD Data radio signal by multiplying the polarity change signal by the FD Data radio signal;

[0034] - formation of the Extended Phase Detector (EPD) signal using the weighted summation of the corrected PD Data radio signal and the PD Pilot radio signal to close the feedback loop.

[0035] The second claimed method of phase synchronization of a multiplex signal includes:

[0036] - reception of a Pilot radio signal and a Data radio signal, including the formation of in-phase and quadrature components of these signals; - formation of a Phase Detector (PD) signal of a Data radio signal using the in-phase and quadrature components of the Data radio signal;

[0037] - formation of the FD Pilot radio signal using the in-phase and quadrature components of the Pilot radio signal;

[0038] - closing the feedback loop through a chain of blocks consisting of a loop filter, NCO and correlators that generate in-phase and quadrature components of the Data radio signal and the Pilot radio signal; and is characterized in that the signal of the Extended Phase Detector (EPD) is formed by weighted summation of the PD signal of the Data radio signal and the PD signal of the Pilot radio signal to close the feedback loop.

[0039] The above methods can be implemented in appropriate devices.

[0040] The first claimed device for phase synchronization of a multiplex signal includes an analog part of a receiver, an analog-to-digital converter, a set of correlators, phase detectors of Data and Pilot radio signals, a loop filter, a generator of a reference pseudo-random sequence (PRS), an NCO oscillator with numerical control, a delay tracking circuit; and is distinguished by the fact that:

[0041] - contains a block for determining the polarity change signal, a block for correcting the FD Data radio signal and a block for weight summation;

[0042] - a block containing the analog part of the receiver, ADC and a set of correlators, is connected to the PD block of the Pilot radio signal by a signal line for transmitting the in-phase component of the Pilot radio signal and a line for transmitting the quadrature component of the Pilot radio signal;

[0043] - a block containing the analog part of the receiver, the ADC and a set of correlators, is connected to the FD block of the Data radio signal by a signal line for transmitting the in-phase component of the Data radio signal and a line for transmitting the quadrature component of the Data radio signal;

[0044] - a block containing the analog part of the receiver, ADC and a set of correlators, is connected to the block for determining the polarity change signal by the signal line for transmitting the in-phase component of the Pilot radio signal;

[0045] - the FD Data radio signal block is connected to the FD Data radio signal correction block by a signal line transmitting the value of the FD Data radio signal output signal;

[0046] - the polarity change signal detection unit is connected to the FD Data radio signal correction unit by the polarity change signal transmission line;

[0047] - the FD Pilot radio signal block is connected to the weight summation block by the transmission line of the FD Pilot radio signal output signal;

[0048] - the FD Data radio signal correction unit is connected by a transmission line of the output corrected FD Data radio signal to the weight summation unit;

[0049] - the weight summation block is connected to the loop filter block by the transmission line of the output signal of the extended phase detector (EPD).

[0050] The second claimed device for phase synchronization of a multiplex signal includes an analog part of a receiver, an analog-to-digital converter, a set of correlators, phase detectors of Data and Pilot radio signals, a loop filter, a reference pseudo-random sequence (PRS) generator, a numerically controlled NCO oscillator, a delay tracking circuit; and is distinguished by the fact that:

[0051] - contains a weight summation block;

[0052] - a block containing the analog part of the receiver, ADC and a set of correlators, is connected to the PD block of the Pilot radio signal by a signal line for transmitting the in-phase component of the Pilot radio signal and a line for transmitting the quadrature component of the Pilot radio signal;

[0053] - a block containing the analog part of the receiver, the ADC and a set of correlators, is connected to the FD block of the Data radio signal by a signal line for transmitting the in-phase component of the Data radio signal and a line for transmitting the quadrature component of the Data radio signal;

[0054] - the FD Data radio signal block is connected to the weight summation block by a signal line transmitting the output signal of the FD Data radio signal;

[0055] - the FD Pilot radio signal block is connected to the weight summation block by a signal line transmitting the output signal of the FD Pilot radio signal;

[0056] - the weight summation block is connected to the loop filter block by the RFD output signal transmission line.

[0057] Additional variants of methods and devices are described below.

[0058] List of drawing figures

[0059] Fig. 1 shows a phase-locked loop (PLL) circuit with an extended phase detector (EPD).

[0060] Fig. 2 shows the diagram of a phased array transducer with a radio frequency detector (RFD) in a variant without changing the polarity of the RF Data radio signal using the in-phase component of the Pilot radio signal.

[0061] Description of the invention implementation

[0062] The claimed invention can be implemented as follows.

[0063] A typical phase-locked loop system (including a typical phase-locked loop system) can be represented as consisting of three main blocks: a discriminator (in the case of a phase-locked loop, a phase-locked loop), a loop filter, and a reference signal generator. Variant #1, described previously, uses a phase-locked loop with a narrow arctangent, while Variant #2 uses a phase-locked loop with a wide arctangent. The proposed variant differs from Variants #1 and #2 by replacing the "typical" phase-locked loops in Variants #1 and #2 with an extended phase detector.

[0064] Figure 1 shows a block diagram of the proposed invention. In Figure 1, the RFD block is outlined with a dotted line and designated 111. The remaining blocks, not outlined with a dotted line, are known in the art and are not new.

[0065] Signal processing is carried out as follows.

[0066] The multiplexed radio signal received from antenna 101 is processed in block 102, which contains the analog receiver section, an ADC, and a set of correlators. Each multiplexed radio signal from each satellite has its own set of correlators.

[0067] Fig. 1 shows the processing of two radio signals from one satellite: Pilot (without modulation by a priori unknown binary information symbols) and Data (with inverse modulation by a priori unknown binary information symbols μ b- data stream according to the terminology of the patent for variant No. 3). In each of the correlators, the converted input radio signal is multiplied by the corresponding reference signal and the result of the multiplication is accumulated during the i-th control period of the synchronization systems (PAC and NCCS - delay tracking circuits). The NCCS is not shown in Fig. 1 in order not to complicate the figure. The NCCS generates a reference pseudo-random sequence (PRS) fed to block 102. This block 102 is also fed with in-phase (with respect to the Pilot radio signal) and quadrature reference harmonic signals from block 110 (NCO - numerically controlled oscillator).

[0068] At the two upper outputs of block 102, the in-phase (I) cleared from the data stream is output. b i ) and quadrature (Q b i ) Data components of the radio signal.

[0069] In the first of the variants of the implementation of the claimed method, the data stream is cleared by multiplying the one-millisecond in-phase and quadrature components of the Data radio signal by the estimates of μ b a priori unknown binary symbols These purified one-millisecond The components are then accumulated over the control period, and thus the values ​​are obtained. In more detail, the implementation of this processing is described for example in patent US8.368.593.

[0070] If the Pilot radio signal is not modulated by a secondary binary code (for example, the QZSS L2CL signal), then the two lower outputs of block 102 produce a common-mode signal and quadrature components of Pilot radio signal.

[0071] If the Pilot radio signal is modulated by a secondary binary code, then the two lower outputs of block 102 output the in-phase and quadrature signals cleared of the secondary code. Pilot radio signal components.

[0072] In one embodiment, secondary code removal occurs by multiplying the one-millisecond in-phase and quadrature components of the Pilot radio signal by a priori known values These purified one-millisecond components are then accumulated over the control period, and thus the quantities ? and The implementation of this processing is described in more detail, for example, in patent US8.368.593.

[0073] Block 108 can be constructed in the same way as it is constructed in the well-known FAP scheme b , described earlier.

[0074] Block 108 uses a narrow arctangent phase detector (arctg), the output signal of which is calculated using the formula:

[0075] (1)

[0076] (2)

[0077] Here f c f c

[0078] In case 1, formulas (2) and (1) are simplified and take the form:

[0079] The variant described by formulas (l)-(2) will be conventionally called the variant with averaging of the denominator (UD), and the variant described by formula (1*) will be called the variant without UD.

[0080] At high SNRs, the properties of the ultrasonic and non-ultrasonic variants are virtually identical. However, at low SNRs, the use of ultrasonics is essential: it helps lower the SNR threshold, i.e., the SNR value below which phase jumps (cycle slips - CS) and / or even complete synchronization failure begin.

[0081] Block 103 can be constructed as follows. Signal F on the output of block 103 can be calculated using the formula (conditionally - the version with ultrasound):

[0082] (3) where the value is calculated using the formula:

[0083] (4) Here . In this case, formula (4) is similar to formula (2), but in (4) the coefficient appears, which in the general case may differ from coefficient f in formula (2), but they can also be equal to each other (for example,

[0084] In the case of formula (4) and (3) they are simplified and take the form (option without ultrasound):

[0085] (4*)

[0086] (3*)

[0087] Block 106 (if there is an ultrasound) can be constructed in accordance with formula (5): (5) where S[ is the polarity change signal generated at the output of block 106.

[0088] In one embodiment, block 106 (without ultrasound) can be constructed using the formula:

[0089] (5*)

[0090] In block 109, the FD Data radio signal is multiplied by the signal changing the polarity obtained at the output of block 106, thereby The output of block 109 produces a signal - the corrected FD signal Radio signal data.

[0091] (6)

[0092] Blocks 106 and 109 in Fig. 1 allow for better dynamic properties of FAP systems with RFD.

[0093] In cases where only better noise immunity of the PLL is required (but not better dynamic properties), blocks 106 and 109 can be excluded from the circuit, resulting in a circuit of the PLL with RFD in a version without changing the polarity of the FD Data radio signal using the in-phase component of the Pilot radio signal, shown in Fig. 2.

[0094] In block 104, weighted summation of signals occurs (on Fig.1) or signals This weight summation is done with using weighting factors w t and (1 — w t ), which will be described below. As a result, the formula for the Zf signal at the output of block 111 of the extended PD will look like this:

[0095] (7)

[0096] In the embodiment, in the presence of ultrasound, after substituting the expressions for according to formulas (3)-(4), (1)-(2) and (5), expression (7) takes the form:

[0097] (7*) The signal from formula (7) is used in the same way as the signal z conventional FD in a conventional FAP system. Namely, the signal goes to a loop filter (block 105), at the output of which a control signal is generated, which reconfigures the frequency and phase of the quadrature harmonic reference signals generated by the NCO block (block 110), described earlier.

[0098] At w t = 1 synchronization is performed only by the Pilot radio signal. This corresponds to the previously mentioned option #2.

[0099] Let us consider the option of equal power of the Pilot and Data radio signals, and the choice of equal (and constant) weights in formula (7):

[0100] (8)

[0101] In this case, both the minimum error in tracking the full phase of the incoming radio signal and the minimum noise error in measuring the full phase (3 dB less than in the case w) are ensured. This possible only in the linear mode of operation of the PLL, at relatively high SNR.

[0102] In the nonlinear (from the point of view of reducing the SNR threshold value) mode with equal powers of the Pilot and Data radio signals, the weight must be increased: (9)

[0103] In one embodiment of the claimed solution, the weight of the FD Pilot radio signal (w) and, accordingly, the weight of the corrected FD Data radio signal (1 - w) can be chosen to be constant over time (i.e., independent of the control period number i). The specific values ​​of the weights w and 1 - w can be chosen differently depending on what is more important: minimizing the SNR threshold value or minimizing the noise error in estimating the total phase in the linear FAL operating mode. In cases where it is necessary to minimize both values, the weight w t and can be selected depending on the SNR estimate for the i-th period control (for example, calculated using the Pilot radio signal).

[0104] In this case, when the power of the Pilot radio signal increases or decreases compared to the power of the Data radio signal, the weighting factor should be increased or decreased accordingly.

[0105] If it is known in advance that the powers of the Pilot and Data radio signals are the same, then in formula (1) the variable can be replaced by At equal powers, this option is “theoretically the best”, since the mathematical expectation of the variables is the same, and the standard deviation of the value less than the standard deviation of the quantity

[0106] The RFD variant using formula (1) is more universal in relation to the “theoretically better” variant, since it can be applied at any ratio of the Pilot and Data radio signal powers.

[0107] The described methods can be implemented in corresponding devices operating in the described modes.

Claims

Formula 1. A method for phase synchronization of a multiplex signal, including: - reception of the Pilot radio signal and the Data radio signal, including the formation of in-phase and quadrature components of these signals; - formation of the Phase Detector (PD) signal of the Data radio signal using the in-phase and quadrature components of the Data radio signal; - formation of the FD Pilot radio signal using the in-phase and quadrature components of the Pilot radio signal; - closing the feedback loop through a chain of blocks consisting of a loop filter, NCO and correlators that generate in-phase and quadrature components of the Data radio signal and the Pilot radio signal; characterized in that it includes: - formation of a signal for changing the polarity of the FD Data radio signal using the in-phase component of the Pilot radio signal; - formation of a corrected FD Data radio signal by multiplying the polarity change signal by the FD Data radio signal; - formation of the Extended Phase Detector (EPD) signal using the weighted summation of the corrected PD Data radio signal and the PD Pilot radio signal to close the feedback loop.

2. The method according to paragraph 1, characterized in that the FD Data signal of the radio signal is formed as a narrow arctangent of the ratio of the quadrature component of the Data radio signal, cleared from the data stream, to the in-phase component of the same radio signal, cleared from the data stream.

3. The method according to paragraph 1, characterized in that the FD Data radio signal is formed as a narrow arctangent of the ratio of the quadrature component of the Data radio signal, cleared from the data stream, to the filtered in-phase component of the same Data radio signal.

4. The method according to paragraph 3, characterized in that the filtered in-phase component Data of the radio signal is formed at the output of a first-order digital filter, to the input of which the in-phase component Data of the radio signal, cleared from the data stream, is fed.

5. The method according to paragraph 1, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the FD signal of the Pilot radio signal is formed as a wide arctangent of the following two arguments: the quadrature component of the Pilot radio signal and the in-phase component of the same Pilot radio signal.

6. The method according to paragraph 1, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the FD signal of the Pilot radio signal is formed as a wide arctangent of the following two arguments: the quadrature component of the Pilot radio signal and the filtered in-phase component of the same Pilot radio signal.

7. The method according to claim 6, characterized in that the filtered in-phase component of the Pilot radio signal is formed at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal is fed.

8. The method according to claim 1, characterized in that in the case where the Pilot radio signal is modulated by a secondary code, the FD signal of the Pilot radio signal is formed as a wide arctangent of the following two arguments: the quadrature component of the Pilot radio signal cleared of the secondary code and the in-phase component of the same Pilot radio signal cleared of the secondary code.

9. The method according to claim 1, characterized in that in the case where the Pilot radio signal is modulated by a secondary code, the FD signal of the Pilot radio signal is formed as a wide arctangent of the following two arguments: the quadrature component of the Pilot radio signal cleared of the secondary code and the filtered in-phase components of the same Pilot radio signal.

10. The method according to claim 9, characterized in that the filtered in-phase component of the Pilot radio signal is formed at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal, cleared of the secondary code, is fed.

11. The method according to claim 1, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the signal for changing the polarity of the FD Data radio signal is formed as an estimate of the sign of the in-phase component of the Pilot radio signal.

12. The method according to claim 1, characterized in that in the event that the Pilot radio signal is modulated by a secondary code, the signal for changing the polarity of the FD Data radio signal is formed as an estimate of the sign of the in-phase component of the Pilot radio signal, cleared of the secondary code.

13. The method according to claim 1, characterized in that the signal for changing the polarity of the FD Data signal of the radio signal is formed as an estimate of the sign of the filtered in-phase component Pilot of the radio signal.

14. The method according to paragraph 13, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the filtered in-phase component of the Pilot radio signal is formed at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal is fed.

15. The method according to paragraph 13, characterized in that in the case where the Pilot radio signal is modulated by a secondary code, the filtered in-phase component of the Pilot radio signal is formed at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal, cleared of the secondary code, is fed.

16. The method according to paragraph 1, characterized in that the RFD signal is formed by weighted summation of the corrected FD Data signal of the radio signal, taken with a weight of 1-W i , and the FD Pilot radio signal, taken with the weight Wi.

17. The method according to claim 16, characterized in that the weight w is selected depending on the SNR estimate for the Pilot radio signal. 18, The method according to item 16, characterized in that the weight W i is chosen to be constant in time Wi=w and independent of the control period number i, while the weight is chosen in the range 0.5 ≤ w < 1.

19. A method for phase synchronization of a multiplex signal, including: - reception of the Pilot radio signal and the Data radio signal, including the formation of in-phase and quadrature components of these signals; - formation of the Phase Detector (PD) signal of the Data radio signal using the in-phase and quadrature components of the Data radio signal; - formation of the FD Pilot radio signal using the in-phase and quadrature components of the Pilot radio signal; - closing the feedback loop through a chain of blocks consisting of a loop filter, NCO and correlators that generate in-phase and quadrature components of the Data radio signal and the Pilot radio signal; characterized in that: the Extended Phase Detector (EPD) signal is formed by weighted summation of the PD signal of the Data radio signal and the PD signal of the Pilot radio signal to close the feedback loop.

20. The method according to claim 19, characterized in that the FD Data signal of the radio signal is formed as a narrow arctangent of the ratio of the quadrature component of the Data radio signal, cleared from the data stream, to the in-phase component of the same radio signal, cleared from the data stream.

21. The method according to claim 19, characterized in that the FD Data radio signal is formed as a narrow arctangent of the ratio of the quadrature component of the Data radio signal, cleared from the data stream, to the filtered in-phase component of the same Data radio signal.

22. The method according to paragraph 21, characterized in that the filtered in-phase component Data of the radio signal is formed at the output of a first-order digital filter, to the input of which the in-phase component Data of the radio signal, cleared from the data stream, is fed. 23, The method according to claim 19, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the FD signal of the Pilot radio signal is formed as a wide arctangent of the following two arguments: the quadrature component of the Pilot radio signal and the in-phase component of the same Pilot radio signal.

24. The method according to claim 19, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the FD signal of the Pilot radio signal is formed as a wide arctangent of the following two arguments: the quadrature component of the Pilot radio signal and the filtered in-phase component of the same Pilot radio signal.

25. The method according to paragraph 24, characterized in that the filtered in-phase component of the Pilot radio signal is formed at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal is fed.

26. The method according to claim 19, characterized in that in the case where the Pilot radio signal is modulated by a secondary code, the FD signal of the Pilot radio signal is formed as a wide arctangent of the following two arguments: the quadrature component of the Pilot radio signal cleared of the secondary code and the in-phase component of the same Pilot radio signal cleared of the secondary code.

27. The method according to claim 19, characterized in that in the case where the Pilot radio signal is modulated by a secondary code, the FD signal of the Pilot radio signal is formed as a wide arctangent of the following two arguments: the quadrature component of the Pilot radio signal cleared of the secondary code and the filtered in-phase component of the same Pilot radio signal.

28. The method according to paragraph 27, characterized in that the filtered in-phase component of the Pilot radio signal is formed at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal, cleared of the secondary code, is fed. 29, The method according to item 19, characterized in that the RFD signal is formed using the weighted summation of the FD Data signal of the radio signal, taken with a weight of 1— W i , and the FD Pilot radio signal, taken with weight W i . 30, The method according to paragraph 29, characterized in that the weight w is selected depending on the SNR estimate for the Pilot radio signal. 31, The method according to paragraph 29, characterized in that the weight W i choose w to be constant in time i =w and independent of the control period number i, while the weight is selected in the range: 0.5 ≤ w < 1.

32. A device for phase synchronization of a multiplex signal, comprising an analog section of a receiver, an analog-to-digital converter, a set of correlators, phase detectors (PD) for Data and Pilot radio signals, a loop filter, a reference pseudo-random sequence (PRS) generator, a numerically controlled NCO oscillator, and a delay tracking circuit; characterized in that: - contains a block for determining the polarity change signal, a block for correcting the FD Data radio signal and a block for weight summation; - a block containing the analog part of the receiver, ADC and a set of correlators, is connected to the PD block of the Pilot radio signal by a signal line for transmitting the in-phase component of the Pilot radio signal and a line for transmitting the quadrature component of the Pilot radio signal; - a block containing the analog part of the receiver, the ADC and a set of correlators, is connected to the FD block of the Data radio signal by a signal line for transmitting the in-phase component of the Data radio signal and a line for transmitting the quadrature component of the Data radio signal; - a block containing the analog part of the receiver, ADC and a set of correlators, is connected to the block for determining the polarity change signal by the signal line for transmitting the in-phase component of the Pilot radio signal; - the FD Data radio signal block is connected to the FD Data radio signal correction block by a signal line transmitting the value of the FD Data radio signal output signal; - the polarity change signal detection unit is connected to the FD Data radio signal correction unit by the polarity change signal transmission line; - the FD Pilot radio signal block is connected to the weight summation block by the output signal transmission line of the FD Pilot radio signal; - the FD Data radio signal correction unit is connected by a transmission line of the output corrected FD Data radio signal to the weight summation unit; - the weight summation block is connected to the loop filter block by the transmission line of the output signal of the extended phase detector (EPD).

33. The device according to item 32, characterized in that the FD Data radio signal block is designed with the ability to calculate the narrow arctangent of the ratio of the quadrature component of the Data radio signal, cleared from the data stream, to the in-phase component of the same radio signal, cleared from the data stream.

34. The device according to item 32, characterized in that the FD Data radio signal block perform with the ability to calculate the narrow arctangent of the ratio of the quadrature component of the Data radio signal, cleared from the data stream, to the filtered in-phase component of the same Data radio signal. 35, The device according to item 34, characterized in that the FD Data radio signal block is designed with the possibility of obtaining a filtered in-phase component Data of the radio signal at the output of a first-order digital filter, to the input of which the in-phase component Data of the radio signal, cleared from the data stream, is fed.

36. The device according to item 32, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the FD block of the Pilot radio signal is designed with the possibility of calculating a wide arctangent from the following two arguments: the quadrature component of the Pilot radio signal and the in-phase component of the same Pilot radio signal.

37. The device according to item 32, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the FD block of the Pilot radio signal is designed with the ability to calculate a wide arctangent from the following two arguments: the quadrature component of the Pilot radio signal and the filtered in-phase component of the same Pilot radio signal.

38. The device according to item 37, characterized in that the Pilot radio signal FD unit is designed with the possibility of obtaining a filtered in-phase component of the Pilot radio signal at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal is fed.

39. The device according to item 32, characterized in that in the case where the Pilot radio signal is modulated by a secondary code, the FD block of the Pilot radio signal is designed with the possibility of calculating a wide arctangent from the following two arguments: the quadrature component of the Pilot radio signal cleared of the secondary code and cleared of the secondary code of the common-mode component of the same Pilot radio signal.

40. The device according to item 32, characterized in that in the event that the Pilot radio signal is modulated by a secondary code, the FD block of the Pilot radio signal is designed with the possibility of calculating a wide arctangent from the following two arguments: the quadrature component of the Pilot radio signal cleared of the secondary code and the filtered in-phase component of the same Pilot radio signal.

41. The device according to item 40, characterized in that the Pilot radio signal FD unit is designed with the possibility of obtaining a filtered in-phase component of the Pilot radio signal at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal, cleared of the secondary code, is fed.

42. The device according to item 32, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the polarity change signal determination unit is configured to generate a signal for changing the polarity of the FD Data radio signal as an estimate of the sign of the in-phase component of the Pilot radio signal.

43. The device according to paragraph 32, characterized in that in the event that the Pilot radio signal is modulated by a secondary code, the polarity change signal determination unit is configured to generate a signal for changing the polarity of the FD Data radio signal as an estimate of the sign of the in-phase component of the Pilot radio signal, cleared of the secondary code.

44. The device according to item 32, characterized in that the polarity change signal determination unit is designed with the possibility of generating a signal for changing the polarity of the FD Data signal of the radio signal as an estimate of the sign of the filtered in-phase component of the Pilot radio signal.

45. The device according to item 44, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the polarity change signal determination unit is designed with the possibility of obtaining a filtered in-phase component of the Pilot radio signal at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal is fed.

46. ​​The device according to item 44, characterized in that in the event that the Pilot radio signal is modulated by a secondary code, the polarity change signal determination unit is designed with the possibility of obtaining a filtered in-phase component of the Pilot radio signal at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal, cleared of the secondary code, is fed. 47, The device according to item 32, characterized in that the weight summation unit is designed with the possibility of generating a RFD signal as a weight summation of the corrected FD Data signal of the radio signal, taken with a weight of 1-w, and the FD Pilot signal of the radio signal, taken with a weight of w>. 48, The device according to item 47, characterized in that the weight summation block is designed with the possibility of selecting the weight w, depending on the SNR estimate for the Pilot radio signal.

49. The device according to item 47, characterized in that the weight summation block is designed with the possibility of selecting a weight w>, constant in time Wi=w, independent of the control period number i and in the range: 0.5 ≤ w < 1. 50, A multiplex signal phase synchronization device that includes an analog receiver section, an analog-to-digital converter, a set of correlators, phase detectors (PD) for Data and Pilot radio signals, a loop filter, a reference pseudo-random sequence (RRS) generator, a numerically controlled NCO oscillator, a circuit delay monitoring; characterized in that: - contains a weight summation block; - a block containing the analog part of the receiver, ADC and a set of correlators, is connected to the PD block of the Pilot radio signal by a signal line for transmitting the in-phase component of the Pilot radio signal and a line for transmitting the quadrature component of the Pilot radio signal; - a block containing the analog part of the receiver, the ADC and a set of correlators, is connected to the FD block of the Data radio signal by a signal line for transmitting the in-phase component of the Data radio signal and a line for transmitting the quadrature component of the Data radio signal; - the FD Data radio signal block is connected to the weight summation block by a signal line transmitting the output signal of the FD Data radio signal; - the FD Pilot radio signal block is connected to the weight summation block by a signal line transmitting the output signal of the FD Pilot radio signal; - the weight summation block is connected to the loop filter block by the transmission line of the output signal of the extended phase detector (EPD).

51. The device according to item 50, characterized in that the FD Data radio signal block is designed with the ability to calculate the narrow arctangent of the ratio of the quadrature component of the Data radio signal, cleared from the data stream, to the in-phase component of the same radio signal, cleared from the data stream.

52. The device according to item 50, characterized in that the FD Data radio signal block is designed with the ability to calculate the narrow arctangent of the ratio of the quadrature component of the Data radio signal, cleared from the data stream, to the filtered in-phase component of the same Data radio signal.

53. The device according to item 52, characterized in that the FD Data radio signal block is designed with the possibility of receiving a filtered in-phase component of the Data radio signal at the output of the first-order digital filter, at the input which feeds the in-phase Data component of the radio signal, cleared of data stream.

54. The device according to item 50, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the FD block of the Pilot radio signal is designed with the possibility of calculating a wide arctangent from the following two arguments: the quadrature component of the Pilot radio signal and the in-phase component of the same Pilot radio signal.

55. The device according to item 50, characterized in that in the event that the Pilot radio signal is not modulated by a secondary code, the FD block of the Pilot radio signal is designed with the possibility of calculating a wide arctangent from the following two arguments: the quadrature component of the Pilot radio signal and the filtered in-phase component of the same Pilot radio signal. 56, The device according to item 55, characterized in that the Pilot radio signal FD block is designed with the possibility of obtaining a filtered in-phase component of the Pilot radio signal at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal is fed.

57. The device according to item 50, characterized in that in the event that the Pilot radio signal is modulated by a secondary code, the FD block of the Pilot radio signal is designed with the ability to calculate a wide arctangent from the following two arguments: the quadrature component of the Pilot radio signal cleared of the secondary code and the in-phase component of the same Pilot radio signal cleared of the secondary code.

58. The device according to item 50, characterized in that in the case where the Pilot radio signal is modulated by a secondary code, the FD block of the Pilot radio signal is designed with the possibility of calculating a wide arctangent from the following two arguments: the quadrature component of the Pilot radio signal cleared of the secondary code and filtered common-mode component of the same Pilot radio signal.

59. The device according to item 58, characterized in that the Pilot radio signal FD unit is designed with the possibility of obtaining a filtered in-phase component of the Pilot radio signal at the output of a first-order digital filter, to the input of which the in-phase component of the Pilot radio signal, cleared of the secondary code, is fed.

60. The device according to item 50, characterized in that the weight summation unit is designed with the possibility of generating a RFD signal as a weight summation of the FD Data signal of the radio signal, taken with the weight 1-Wi, and the FD Pilot signal of the radio signal, taken with the weight w;. 61, The device according to item 60, characterized in that the weight summation block is designed with the possibility of selecting the weight w, depending on the SNR estimate for the Pilot radio signal.

62. The device according to item 60, characterized in that the weight summation unit is designed with the possibility of selecting a weight Wi, constant over time W i =w, independent of the control period number i and in the range: 0.5 ≤ w < 1.

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