Voltage conversion circuit, charging management module and electronic equipment

Abstract

This application provides a voltage conversion circuit, a charging management module, and an electronic device, relating to the field of electronic technology, which can improve the severe overheating problem caused by uneven current distribution. The voltage conversion circuit includes: a first switching unit connected in series between the input terminal and a first node; a second switching unit connected in series between the first node and a second node; a first capacitor unit connected in series between the first node and a third node; a second capacitor unit connected in series between the second node and a fourth node; a third switching unit connected in series between the third node and a fifth node; a fourth switching unit connected in series between the third node and a ground terminal; a fifth switching unit connected in series between the fifth node and an output terminal; a third capacitor unit connected in series between the fifth node and a sixth node; a sixth switching unit connected in series between the sixth node and the output terminal; a seventh switching unit; an eighth switching unit; a ninth switching unit; and a tenth switching unit.

Description

Technical Field

[0001] This application relates to the field of electronic technology, and in particular to a voltage conversion circuit, a charging management module, and an electronic device. Background Technology

[0002] With the development of electronic technology, the performance requirements for voltage converters are getting higher and higher. For example, in the field of mobile phones, fast charging is a way to solve the problem of short battery life. Fast charging means increased charging current. To adapt to the larger charging current, a voltage converter with a voltage gain of 4:1 can be used.

[0003] For example, such as Figure 1 As shown, the current Dickson converter can achieve a voltage gain of 4:1 and has high efficiency. However, the uneven current distribution in the circuit leads to severe overheating of some transistors in high current output scenarios. Summary of the Invention

[0004] A voltage conversion circuit, a charging management module, and an electronic device are provided to improve the problem of severe overheating caused by uneven current distribution.

[0005] In a first aspect, a voltage conversion circuit is provided, comprising: a first switching unit, the first terminal of which is electrically connected to an input terminal; a second switching unit, the first terminal of which is electrically connected to a second terminal of the first switching unit; a first capacitor unit, the first terminal of which is electrically connected to the second terminal of the first switching unit; a second capacitor unit, the first terminal of which is electrically connected to the second terminal of the second switching unit; a third switching unit, the first terminal of which is electrically connected to the second terminal of the first capacitor unit; a fourth switching unit, the first terminal of which is electrically connected to the second terminal of the first capacitor unit, and the second terminal of the fourth switching unit is electrically connected to a ground terminal; a fifth switching unit, the first terminal of which is electrically connected to the second terminal of the third switching unit; and a third capacitor unit, the first terminal of which is electrically connected to the second terminal of the third switching unit. The first terminal of the sixth switch unit is electrically connected to the second terminal of the third capacitor unit, and the second terminal of the sixth switch unit is electrically connected to the second terminal of the fifth switch unit; the first terminal of the seventh switch unit is electrically connected to the second terminal of the third capacitor unit, and the second terminal of the seventh switch unit is electrically connected to the ground terminal; the first terminal of the eighth switch unit is electrically connected to the second terminal of the second switch unit, and the second terminal of the eighth switch unit is electrically connected to the output terminal; the first terminal of the ninth switch unit is electrically connected to the second terminal of the second capacitor unit, and the second terminal of the ninth switch unit is electrically connected to the output terminal; the first terminal of the tenth switch unit is electrically connected to the second terminal of the second capacitor unit, and the second terminal of the tenth switch unit is electrically connected to the ground terminal.

[0006] In one possible implementation, when the voltage conversion circuit is in operation, it operates in a periodic series of time periods, each of which includes a first time period and a second time period. In the first time period, the first, third, sixth, eighth, and tenth switching units are turned on, while the second, fourth, fifth, seventh, and ninth switching units are turned off. In the second time period, the first, third, sixth, eighth, and tenth switching units are turned off, while the second, fourth, fifth, seventh, and ninth switching units are turned on.

[0007] In one possible implementation, the first switching unit, the second switching unit, the third switching unit, the fourth switching unit, the fifth switching unit, the sixth switching unit, the seventh switching unit, the eighth switching unit, the ninth switching unit, and the tenth switching unit are metal-oxide-semiconductor field-effect transistors (MOSFETs), gallium nitride (GaN) transistors, silicon carbide (SiC) transistors, insulated-gate bipolar transistors (IGBTs), or relays.

[0008] In one possible implementation, the voltage conversion circuit further includes: an anti-reverse transistor connected in series between the input terminal and the first switching unit, wherein the parasitic diode of the anti-reverse transistor is oriented in a first direction, and the parasitic diode of the first switching unit is oriented in a second direction, wherein the first direction is opposite to the second direction.

[0009] Secondly, a charging management module is provided, comprising: the voltage conversion circuit described above, the output terminal of which is electrically connected to the charging and discharging terminal of the battery; and a charging control unit, which is electrically connected to the control terminal of each switching unit in the voltage conversion circuit, and is used to control the voltage conversion circuit to be in a working state or a non-working state.

[0010] In one possible implementation, when the voltage conversion circuit is in a non-operating state, the charging control unit is used to provide a cutoff level to the control terminals of the first switching unit, the second switching unit, the third switching unit, the fourth switching unit, the fifth switching unit, the sixth switching unit, the seventh switching unit, the eighth switching unit, the ninth switching unit, and the tenth switching unit.

[0011] In one possible implementation, the charging management module further includes: a charging circuit electrically connected to the input terminal, the battery charging / discharging terminal, the system operating voltage terminal, and the charging control unit; the charging control unit is used to control the voltage conversion circuit to be in a working state in constant current charging mode, and the charging control unit is also used to control the voltage conversion circuit to be in a non-working state and control the charging circuit to provide charging voltage to the battery charging / discharging terminal in constant voltage charging mode.

[0012] In one possible implementation, the charging management module further includes: a charging circuit electrically connected to the input terminal and the charging control unit at the battery charging / discharging terminal; the charging control unit is used to control the voltage conversion circuit to be in a working state when the charging current is greater than a preset value in constant current charging mode; the charging control unit is also used to control the voltage conversion circuit to be in a non-working state and control the charging circuit to provide charging voltage to the battery charging / discharging terminal when the charging current is not greater than the preset value in constant current charging mode and in constant voltage charging mode.

[0013] In one possible implementation, the charging circuit is also electrically connected to the system operating voltage terminal, and the charging circuit is also used to provide the operating voltage to the system operating voltage terminal.

[0014] Thirdly, an electronic device is provided, including the voltage conversion circuit or the charging management module described above.

[0015] The voltage conversion circuit, charging management module, and electronic device in this application embodiment, through the connection relationship between the switching unit and the capacitor unit, make the current distribution more uniform during the operation of the voltage conversion circuit, improve the serious heat generation problem caused by uneven current distribution, reduce conduction loss, and reduce the withstand voltage of the capacitor unit, thereby reducing the volume of the capacitor unit and improving space utilization. Attached Figure Description

[0016] Figure 1 This is a structural block diagram of an electronic device;

[0017] Figure 2 This is a schematic diagram of the circuit topology of a Dickson converter in the prior art;

[0018] Figure 3 for Figure 2 The circuit diagram includes the equivalent circuit diagram of the transistor in the first time period;

[0019] Figure 4 for Figure 3 The equivalent circuit diagram of the transistor is omitted.

[0020] Figure 5 for Figure 2 The circuit diagram includes the equivalent circuit of the transistor in the second time period;

[0021] Figure 6 for Figure 5 The equivalent circuit diagram of the transistor is omitted.

[0022] Figure 7 This is a schematic diagram of the topology of a voltage conversion circuit in an embodiment of this application;

[0023] Figure 8 for Figure 7 The circuit diagram includes the equivalent circuit diagram of the transistor in the first time period;

[0024] Figure 9 for Figure 8 The equivalent circuit diagram of the transistor is omitted.

[0025] Figure 10 for Figure 7 The circuit diagram includes the equivalent circuit of the transistor in the second time period;

[0026] Figure 11 for Figure 10 The equivalent circuit diagram of the transistor is omitted.

[0027] Figure 12 This is a timing diagram of the control signals for the voltage conversion circuit in an embodiment of this application;

[0028] Figure 13 This is a simulation waveform diagram of a portion of the voltage conversion circuit structure in the embodiments of this application;

[0029] Figure 14 This is a simulation waveform diagram of another part of the voltage conversion circuit structure in the embodiments of this application;

[0030] Figure 15 This is a simulation waveform diagram of another part of the voltage conversion circuit structure in the embodiments of this application;

[0031] Figure 16 This is a schematic diagram comparing the losses between the embodiments of this application and the prior art;

[0032] Figure 17 This is a schematic diagram of the topology of another voltage conversion circuit in an embodiment of this application;

[0033] Figure 18 This is a schematic diagram of the structure of another electronic device in an embodiment of this application. Detailed Implementation

[0034] The terminology used in the implementation section of this application is for the purpose of explaining specific embodiments of this application only, and is not intended to limit this application.

[0035] Before introducing the embodiments of this application, the scenarios involved in the embodiments of this application will be introduced first. The embodiments of this application can be used in scenarios where electronic devices receive external charging input or charge external devices. The electronic devices involved in this application may be mobile phones, tablets, personal computers (PCs), personal digital assistants (PDAs), smartwatches, netbooks, wearable electronic devices, augmented reality (AR) devices, virtual reality (VR) devices, in-vehicle devices, drone devices, smart cars, smart speakers, robots, smart glasses, etc.

[0036] For example, such as Figure 1 As shown, the electronic device 100 may include a processor 110, a charging management module 140, a power management module 141, and a battery 142. It is understood that the structures illustrated in this embodiment do not constitute a specific limitation on the electronic device 100. In other embodiments of this application, the electronic device 100 may include more or fewer components than illustrated, or combine some components, or split some components, or have different component arrangements. The illustrated components may be implemented in hardware, software, or a combination of software and hardware.

[0037] Processor 110 may include one or more processing units, such as application processors (APs), modem processors, graphics processing units (GPUs), image signal processors (ISPs), controllers, video codecs, digital signal processors (DSPs), baseband processors, and / or neural network processing units (NPUs). These different processing units may be independent devices or integrated into one or more processors.

[0038] The controller can generate operation control signals based on the instruction opcode and timing signals to complete the control of instruction fetching and execution.

[0039] The processor 110 may also include a memory for storing instructions and data. In some embodiments, the memory in the processor 110 is a cache memory. This memory can store instructions or data that the processor 110 has just used or that are used repeatedly. If the processor 110 needs to use the instruction or data again, it can retrieve it directly from the memory. This avoids repeated accesses, reduces the waiting time of the processor 110, and thus improves the efficiency of the system.

[0040] In some embodiments, the processor 110 may include one or more interfaces. Interfaces may include an inter-integrated circuit (I2C) interface, an inter-integrated circuit sound (I2S) interface, a pulse code modulation (PCM) interface, a universal asynchronous receiver / transmitter (UART) interface, a mobile industry processor interface (MIPI), a general-purpose input / output (GPIO) interface, a subscriber identity module (SIM) interface, and / or a universal serial bus (USB) interface, etc.

[0041] USB port 130 is a USB standard compliant interface, specifically a Mini USB port, Micro USB port, USB Type-C port, etc. USB port 130 can be used to connect a charger to charge electronic device 100, and can also be used for data transfer between electronic device 100 and peripheral devices. It can also be used to connect headphones for audio playback. This interface can also be used to connect other electronic devices, such as AR devices.

[0042] It is understood that the interface connection relationships between the modules illustrated in the embodiments of the present invention are merely illustrative and do not constitute a structural limitation on the electronic device 100. In other embodiments of this application, the electronic device 100 may also employ different interface connection methods or combinations of multiple interface connection methods as described in the above embodiments.

[0043] The charging management module 140 is used to receive charging input from a charger. The charger can be a wireless charger or a wired charger. In some wired charging embodiments, the charging management module 140 can receive charging input from the wired charger via the USB interface 130. In some wireless charging embodiments, the charging management module 140 can receive wireless charging input via the wireless charging coil of the electronic device 100. Figure 1 The dashed arrow indicates the direction of wireless charging input. While charging the battery 142, the charging management module 140 can also supply power to the electronic device via the power management module 141. Additionally, in other possible implementations, the electronic device 100 can also reverse charge externally via the charging management module 140.

[0044] The power management module 141 connects the battery 142, the charging management module 140, and the processor 110. The power management module 141 receives input from the battery 142 and / or the charging management module 140, providing power to the processor 110, internal memory 121, display screen 194, camera 193, and wireless communication module 160, etc. The power management module 141 can also monitor parameters such as battery capacity, battery cycle count, and battery health status (leakage current, impedance). In some other embodiments, the power management module 141 may also be located within the processor 110. In other embodiments, the power management module 141 and the charging management module 140 may be located in the same device.

[0045] Before introducing the embodiments of this application, the technical problems in the prior art will first be explained, such as... Figures 2-6 As shown, the Dickson converter includes eight transistors (Q01-Q08), three capacitors (C01-C03), and an output filter capacitor (C0). The Dickson converter operates in multiple periodic time periods, each consisting of a first time period and a second time period. In the first time period, Q01, Q03, Q05, and Q08 are turned on, while Q02, Q04, Q06, and Q07 are turned off. In the second time period, Q01, Q03, Q05, and Q08 are turned off, while Q02, Q04, Q06, and Q07 are turned on. Through this switching process between the two time periods, voltage conversion is achieved, transforming the input voltage Vin at the input terminal into the output voltage Vout at the output terminal. The withstand voltage of Q01, Q04, Q05, Q06, Q07, and Q08 is Vout, and the withstand voltage of Q02 and Q03 is twice Vout. Through circuit analysis, it can be seen that... Figure 3 and 4 As shown, in the first time period, the current in both the branch containing C03 and the branch containing C01 passes through Q05, as... Figure 5 and 6As shown, in the second time period, the current in both the branch containing C03 and the branch containing C01 passes through Q06. Therefore, during the entire working process alternating between the first and second time periods, the average current value passing through Q05 or Q06 is twice the average current value passing through other transistors, indicating uneven current distribution. This leads to significant heat generation in transistors Q05 and Q06. Since transistor conduction losses depend on impedance, and impedance is positively correlated with current, the larger current in Q05 and Q06 results in higher conduction losses. To address the aforementioned problems, this application provides a technical solution based on its embodiments. The technical solution of this application's embodiments is described below.

[0046] This application embodiment provides a voltage conversion circuit, which can be the circuit in the charging management module 140 described above, such as... Figure 7As shown, the voltage conversion circuit includes: a first switching unit Q1, with its first terminal electrically connected to the input terminal in; a second switching unit Q2, with its first terminal electrically connected to the second terminal of the first switching unit Q1; a first capacitor unit C1, with its first terminal electrically connected to the second terminal of the first switching unit Q1; a second capacitor unit C2, with its first terminal electrically connected to the second terminal of the second switching unit Q2; a third switching unit Q3, with its first terminal electrically connected to the second terminal of the first capacitor unit C1; a fourth switching unit Q4, with its first terminal electrically connected to the second terminal of the first capacitor unit C1 and its second terminal electrically connected to the ground terminal; a fifth switching unit Q5, with its first terminal electrically connected to the second terminal of the third switching unit Q3; and a third capacitor unit C3, with its first terminal electrically connected to the third capacitor unit C3. The second terminal of switch unit Q3; the first terminal of the sixth switch unit Q6 is electrically connected to the second terminal of the third capacitor unit C3, and the second terminal of the sixth switch unit Q6 is electrically connected to the second terminal of the fifth switch unit Q5; the first terminal of the seventh switch unit Q7 is electrically connected to the second terminal of the third capacitor unit C3, and the second terminal of the seventh switch unit Q7 is electrically connected to the ground terminal; the first terminal of the eighth switch unit Q8 is electrically connected to the second terminal of the second switch unit Q2, and the second terminal of the eighth switch unit Q8 is electrically connected to the output terminal out; the first terminal of the ninth switch unit Q9 is electrically connected to the second terminal of the second capacitor unit C2, and the second terminal of the ninth switch unit Q9 is electrically connected to the output terminal out; the first terminal of the tenth switch unit Q10 is electrically connected to the second terminal of the second capacitor unit C2, and the second terminal of the tenth switch unit Q10 is electrically connected to the ground terminal.The circuit topology is illustrated below by introducing the connection nodes between the various units: First switch unit Q1 is connected in series between the input terminal in and the first node P1; second switch unit Q2 is connected in series between the first node P1 and the second node P2; first capacitor unit C1 is connected in series between the first node P1 and the third node P3; second capacitor unit C2 is connected in series between the second node P2 and the fourth node P4; third switch unit Q3 is connected in series between the third node P3 and the fifth node P5; fourth switch unit Q4 is connected in series between the third node P3 and the ground terminal. The fifth switch unit Q5 is connected in series between the fifth node P5 and the output terminal out; the third capacitor unit C3 is connected in series between the fifth node P5 and the sixth node P6; the sixth switch unit Q6 is connected in series between the sixth node P6 and the output terminal out; the seventh switch unit Q7 is connected in series between the sixth node P6 and the ground terminal; the eighth switch unit Q8 is connected in series between the second node P2 and the output terminal out; the ninth switch unit Q9 is connected in series between the fourth node P4 and the output terminal out; and the tenth switch unit Q10 is connected in series between the fourth node P4 and the ground terminal. Additionally... Figure 7 The diagram also illustrates the output capacitor Cout and the load. The output capacitor Cout is connected in series between the output terminal out and ground to achieve output filtering. The voltage conversion circuit is used to convert the input voltage Vin at the input terminal in into the output voltage Vout at the output terminal out. The output voltage Vout is used to supply the load, which can be, for example, a battery or other device.

[0047] Specifically, such as Figures 8-12 As shown, when the voltage conversion circuit is in operation, it operates in multiple periodic time periods T. Each time period T includes a first time period t1 and a second time period t2. In the first time period t1, the first switching unit Q1, the third switching unit Q3, the sixth switching unit Q6, the eighth switching unit Q8, and the tenth switching unit Q10 are turned on, while the second switching unit Q2, the fourth switching unit Q4, the fifth switching unit Q5, the seventh switching unit Q7, and the ninth switching unit Q9 are turned off. In the second time period t2, the first switching unit Q1, the third switching unit Q3, the sixth switching unit Q6, the eighth switching unit Q8, and the tenth switching unit Q10 are turned off, while the second switching unit Q2, the fourth switching unit Q4, the fifth switching unit Q5, the seventh switching unit Q7, and the ninth switching unit Q9 are turned on. Among these, in... Figure 8 and Figure 10 All switching units in the off state are omitted. It is assumed that each switching unit is an N-type transistor. Figure 12In this diagram, S1 represents the control signal output to the gates of the first switching unit Q1, the third switching unit Q3, the sixth switching unit Q6, the eighth switching unit Q8, and the tenth switching unit Q10. S2 represents the control signal output to the gates of the second switching unit Q2, the fourth switching unit Q4, the fifth switching unit Q5, the seventh switching unit Q7, and the ninth switching unit Q9. For N-type transistors, a high level indicates a conduction level, controlling the corresponding transistor to conduct; a low level indicates a cutoff level, controlling the corresponding transistor to cut off. Figure 12 Signal S1 is used to control the first switch unit Q1, the third switch unit Q3, the sixth switch unit Q6, the eighth switch unit Q8, and the tenth switch unit Q10 to conduct in the first time period t1 and to turn off in the second time period t2. Signal S2 is used to control the second switch unit Q2, the fourth switch unit Q4, the fifth switch unit Q5, the seventh switch unit Q7, and the ninth switch unit Q9 to turn off in the first time period t1 and to conduct in the second time period t2. Theoretically, S1 and S2 are complementary signals with the same duty cycle. Under the theoretically non-dead-zone condition, their duty cycle is 50%. If a dead-zone is included, for example, a 2% dead-zone duty cycle, then the duty cycle of S1 is 49% and the duty cycle of S2 is 49%. The dead-zone refers to the interval when neither S1 nor S2 reaches the conduction level. It should be noted that... Figure 12 The control signals shown are merely examples, and the embodiments of this application do not limit them. The control signals are related to the type of transistor. For example, if the second switching unit Q2 is a P-type transistor, then the control signal corresponding to the second switching unit Q2 can be... Figure 12 In the P-type transistor, S1 represents a low level as the on-state and a high level as the off-state. Therefore, for the second switching unit Q2 of the P-type transistor, using S1 as the gate control signal allows for on-state operation in the first time period t1 and off-state operation in the second time period t2. In other words, this embodiment does not limit the type of switching unit or the specific timing of the control signal, as long as the on-state and off-state corresponding to the first time period t1 and the second time period t2 can be achieved. Furthermore, it should be noted that the voltage conversion circuit in this embodiment can interchange the input terminal in and the output terminal out, i.e., it can convert a 4:1 voltage conversion to a 1:4 voltage conversion. For example, when the voltage conversion circuit is applied in an electronic device, in addition to its normal function of converting externally input voltage for charging, it can also reverse-convert the battery voltage and output it to the external device for reverse charging.

[0048] The circuit will be analyzed below, such as Figures 8-11 As shown, taking the voltage at the input terminal in as Vin and the voltage at the output terminal out as Vout as an example for analysis, in Figure 9As can be seen from the diagram, the second capacitor unit C2 is connected in parallel with the load, therefore their voltages are the same, i.e., the voltage of the second capacitor unit C2 is Vc2 = Vout. Similarly, in... Figure 11 As can be seen from the diagram, the third capacitor unit C3 is connected in parallel with the load, therefore their voltages are the same, i.e., the voltage of the third capacitor unit C3 is Vc3 = Vout. Figure 9 In the diagram, the voltage across the series connection of the first capacitor unit C1, the second capacitor unit C2, and the third capacitor unit C3 is Vin, i.e., Vin = Vc1 + Vc2 + Vc3, where Vc1 is the voltage of the power supply to the first capacitor. Figure 11 We know that Vc1 = Vc2 + Vout. Substituting Vc2 = Vout, Vc3 = Vout, and Vc1 = Vc2 + Vout into Vin = Vc1 + Vc2 + Vc3, we get Vin = 4Vout, that is, the voltage gain Vin:Vout = 4:1. According to the law of conservation of power, the relationship between the input current Iin and the output current Iout is Iin = Iout / 4. Figure 13 As shown in the simulation with an input voltage Vin = 20V, it can be seen that the voltage Vc3 of the third capacitor unit C3 is equal to the output voltage, the voltage Vc2 of the second capacitor unit C2 is equal to the output voltage, the voltage Vc1 of the first capacitor unit C1 is twice the output voltage, and the output voltage Vout is approximately 1 / 4 of the input voltage Vin. However, due to the impedance, parasitic capacitance, and inductance of the components used in the simulation, the output voltage Vout is approximately equal to the theoretical value of 5V, which is a certain deviation. It should be noted that in the actual operation of the circuit, the voltage values ​​corresponding to each component or node are dynamically changing; therefore, the voltages mentioned in the embodiments of this application refer to average voltages. It can be seen that the voltage conversion circuit in the embodiments of this application can achieve a voltage gain of 4:1, and the actual simulation results are consistent with the theoretical analysis. Figure 14 and Figure 15 As shown, Figure 14 The diagram illustrates the voltage waveforms corresponding to signal S1, signal S2, fifth node P5, third node P3, and first node P1. Figure 15The diagram illustrates the voltage waveforms corresponding to signals S1 and S2, the second node P2, the fourth node P4, and the sixth node P6. The voltage difference between the third node P3 and the first node P1 is the voltage Vc1 of the first capacitor unit C1, where Vc1 = 10V, meaning the withstand voltage of the first capacitor unit C1 can be twice Vout. The voltage difference between the fifth node P5 and the sixth node P6 is the voltage Vc3 of the third capacitor unit C3, where Vc3 = 5V, meaning the withstand voltage of the third capacitor unit C3 can be Vout. The voltage difference between the second node P2 and the fourth node P4 is the voltage Vc2 of the second capacitor unit C2, where Vc2 = 5V, meaning the withstand voltage of the second capacitor unit C2 can be Vout. It is evident that the voltage relationships between the nodes are consistent with the theoretical analysis. Furthermore, the voltage difference between the first node P1 and the input terminal in is 0V to 10V, meaning the withstand voltage of the first switching unit Q1 connected in series between them can be twice Vout; the voltage difference between the first node P1 and the second node P2 is 15V to 0V, meaning the withstand voltage of the second switching unit Q2 connected in series between them can be three times Vout; the voltage difference between the third node P3 and the fifth node P5 is 0V to 5V, meaning the withstand voltage of the third switching unit Q3 connected in series between them can be Vout; the voltage difference between the third node P3 and ground is 0V to 10V, meaning the withstand voltage of the fourth switching unit Q4 connected in series between them can be twice Vout; the voltage difference between the fifth node P5 and the output terminal out is 0V to 5V, meaning the withstand voltage of the fifth switching unit Q5 connected in series between them can be three times Vout. The voltage difference between the sixth node P6 and the output terminal out is 0V~5V, meaning the withstand voltage of the sixth switching unit Q6 connected in series between them can be Vout; the voltage difference between the sixth node P6 and ground is 0V~5V, meaning the withstand voltage of the seventh switching unit Q7 connected in series between them can be Vout; the voltage difference between the second node P2 and the output terminal out is 0V~5V, meaning the withstand voltage of the eighth switching unit Q8 connected in series between them can be Vout; the voltage difference between the fourth node P4 and the output terminal out is 0V~5V, meaning the withstand voltage of the ninth switching unit Q9 connected in series between them can be Vout; the voltage difference between the fourth node P4 and ground is 0V~5V, meaning the withstand voltage of the tenth switching unit Q10 connected in series between them can be Vout. Additionally, according to... Figure 8 and Figure 10It can be seen that, regardless of whether it is the first time period t1 or the second time period t2, the current corresponding to the first capacitor unit C1, the second capacitor unit C2, and the third capacitor unit C3 will only pass through one switching unit. There will be no situation where the current corresponding to two capacitor units passes through the same switching unit. Therefore, the current distribution is uniform, and the average current corresponding to each switching unit is equal. Thus, the problem of severe heat generation caused by uneven current distribution is improved. Furthermore, since there is no large current, the conduction loss depends on the impedance, and the impedance is positively correlated with the current value. Therefore, the conduction loss of the entire circuit is small.

[0049] As shown in Table 1, Table 1 lists the voltage conversion circuits in the embodiments of this application. Figure 7 Medium voltage conversion circuit) and the Dickson converter in the prior art ( Figure 2 Parameter comparison table of Dickson converter:

[0050] Table 1

[0051]

[0052] On the one hand, because the current distribution of the voltage conversion circuit in the embodiments of this application is uniform, such as Figure 16 As shown, it illustrates Figure 7 The corresponding circuit (the voltage conversion circuit in the embodiment of this application) and Figure 2 A comparative diagram of losses for the corresponding circuit (the existing Dickson converter) is shown. Both circuits were simulated under conditions of an input voltage of 20V and an output current of 16A. It can be seen that for high-current scenarios, the voltage conversion circuit in this embodiment shows a significant reduction in conduction losses, while the increase in switching losses is relatively small. Since the increase in switching losses is less than the reduction in conduction losses, the overall losses are reduced. Figure 2 Compared to the circuit shown, the overall efficiency of the voltage conversion circuit in this embodiment is improved by approximately 0.7%.

[0053] On the other hand, such as Figure 4 and Figure 9 As shown, compared with the prior art, in the voltage conversion circuit of this application embodiment, the number of capacitor units connected in series between the input terminal in and the output terminal out in the first time period t1 is increased by one. Therefore, the voltage withstand requirement of the capacitor unit is reduced. Figures 2-6 The withstand voltage of C03 in the embodiment of this application is 3 times Vout, while the withstand voltage of C03 in the embodiment of this application is 3 times Vout. Figures 7-11The voltage rating of each capacitor unit in the capacitor is less than 3 times Vout. For example, the voltage rating of the first capacitor unit C1 can be 2 times Vout, the voltage rating of the third capacitor unit C3 can be Vout, and the voltage rating of the second capacitor unit C2 can be Vout. Lower voltage rating requirements can reduce the size of the capacitor units.

[0054] The voltage conversion circuit in this embodiment, through the connection between the switching unit and the capacitor unit, makes the current distribution more uniform during the operation of the voltage conversion circuit, improves the serious heat generation problem caused by uneven current distribution, reduces conduction loss, and reduces the withstand voltage of the capacitor unit, thereby reducing the volume of the capacitor unit and improving space utilization.

[0055] In one possible implementation, the first switching unit Q1, the second switching unit Q2, the third switching unit Q3, the fourth switching unit Q4, the fifth switching unit Q5, the sixth switching unit Q6, the seventh switching unit Q7, the eighth switching unit Q8, the ninth switching unit Q9, and the tenth switching unit Q10 are metal-oxide-semiconductor field-effect transistors (MOSFETs), gallium nitride (GaN) transistors, silicon carbide (SiC) transistors, insulated-gate bipolar transistors (IGBTs), or relays. It is understood that the specific implementation of the above switching units is only an example, as long as the switching function can be controlled to be realized. Taking each switching unit as an example, each switching unit is an independent transistor to realize the switching function. The type of transistor is not limited, for example, it can be a P-type transistor or an N-type transistor. In other feasible implementations, the specific structure of each switching unit is not limited in the embodiments of this application, as long as the switching function can be realized. For example, any switching unit may include multiple transistors connected in series or in series. When all the transistors in the control switching unit are turned on, the switching unit is turned on; when all the transistors in the control switching unit are turned off, the switching unit is turned off.

[0056] Furthermore, the specific structures of the first capacitor unit C1, the second capacitor unit C2, and the third capacitor unit C3 are not limited in the embodiments of this application, as long as they can realize the capacitor function. For example, any capacitor unit may include multiple capacitors connected in parallel or in series.

[0057] In one possible implementation, such as Figure 17As shown, the voltage conversion circuit also includes an anti-reverse current transistor Qf connected in series between the input terminal in and the first switching unit Q1. The parasitic diode of the anti-reverse current transistor Qf (not shown in the figure) is oriented in a first direction, and the parasitic diode of the first switching unit Q1 (not shown in the figure) is oriented in a second direction, with the first direction being opposite to the second direction. Transistors typically have parasitic diodes connected in parallel. Therefore, to prevent reverse current from flowing through the parasitic diodes during the operation of the voltage conversion circuit, an anti-reverse current transistor Qf can be placed between the input terminal in and the first switching unit Q1. For example, if the parasitic diode of the first switching unit Q1 is oriented from the input terminal in to the first node P1, then the parasitic diode of the anti-reverse current transistor Qf is oriented from the first node P1 to the input terminal in. During the operation of the voltage conversion circuit, the anti-reverse current transistor Qf is controlled to conduct, thereby avoiding the influence of the anti-reverse current transistor Qf on the circuit operation. The anti-reverse current function is achieved solely by utilizing the parasitic diode of the anti-reverse current transistor Qf.

[0058] like Figure 18 As shown in the illustration, this application embodiment also provides a charging management module, including: a voltage conversion circuit 10 as described in the above embodiment, the output terminal out of the voltage conversion circuit 10 being electrically connected to the battery charging / discharging terminal Vb, the battery charging / discharging terminal Vb being electrically connected to the positive terminal of the battery, and the negative terminal of the battery being grounded; and a charging control unit 20, the charging control unit 20 being electrically connected to the control terminal of each switching unit in the voltage conversion circuit 10, and the charging control unit 20 being used to control the voltage conversion circuit 10 to be in a working state or a non-working state. This charging management module can be... Figure 1 The charging management module 140 in the middle.

[0059] In one possible implementation, such as Figure 12 and Figure 18As shown, when the voltage conversion circuit 10 is in operation, it operates in multiple periodic time periods T, each time period T including a first time period t1 and a second time period t2. In the first time period t1, the charging control unit 20 provides a conduction level to the control terminals of the first switch unit Q1, the third switch unit Q3, the sixth switch unit Q6, the eighth switch unit Q8, and the tenth switch unit Q10, and provides a cutoff level to the control terminals of the second switch unit Q2, the fourth switch unit Q4, the fifth switch unit Q5, the seventh switch unit Q7, and the ninth switch unit Q9. In the second time period t2, the charging control unit 20 provides a conduction level to the control terminals of the first switch unit Q1, the third switch unit Q3, the sixth switch unit Q6, the eighth switch unit Q8, and the tenth switch unit Q10. The control unit 20 provides a cutoff level to the control terminals of the first switch unit Q1, the second switch unit Q2, the third switch unit Q3, the fourth switch unit Q4, the fifth switch unit Q5, the seventh switch unit Q7, and the ninth switch unit Q9, and provides a conduction level to the control terminals of the second switch unit Q2, the fourth switch unit Q4, the fifth switch unit Q5, the seventh switch unit Q7, and the ninth switch unit Q9. When the voltage conversion circuit 10 is in a non-operating state, the charging control unit 20 provides a cutoff level to the control terminals of the first switch unit Q1, the second switch unit Q2, the third switch unit Q3, the fourth switch unit Q4, the fifth switch unit Q5, the sixth switch unit Q6, the seventh switch unit Q7, the eighth switch unit Q8, the ninth switch unit Q9, and the tenth switch unit Q10.

[0060] Specifically, for example, when each switching unit is a MOSFET, the control terminal of the switching unit refers to the gate of the MOSFET. For an N-type MOSFET, the on-state level is high and the off-state level is low; for a P-type MOSFET, the on-state level is low and the off-state level is high. For example, assuming each switching unit is an N-type MOSFET, in the first time period t1, a high level is output to the gates of Q1, Q3, Q6, Q8, and Q10 to control these transistors to turn on, and a low level is output to the gates of Q2, Q4, Q5, Q7, and Q9 to control these transistors to turn off; in the second time period t2, a low level is output to the gates of Q1, Q3, Q6, Q8, and Q10 to control these transistors to turn off, and a high level is output to the gates of Q2, Q4, Q5, Q7, and Q9 to control these transistors to turn on. The first time period t1 and the second time period t2 alternate gradually to keep the voltage conversion circuit 10 in operation and realize the voltage conversion function. When a low level is continuously output to the gates of Q1 to Q10, these transistors can be controlled to be turned off, that is, the voltage conversion circuit 10 is controlled to be in a non-operating state. It should also be noted that... Figure 17The diagram also illustrates an anti-reverse current transistor Qf. For example, Qf is an N-type transistor. When the voltage conversion circuit 10 is in operation, the charging control unit 20 can provide a high level to the gate of Qf to control Qf to conduct. When the voltage conversion circuit 10 is in a non-operating state, the charging control unit 20 can provide a low level to the gate of Qf to control Qf to be cut off. Alternatively, controlling Qf to be cut off can also put the voltage conversion circuit in a non-operating state.

[0061] In one possible implementation, such as Figure 18 As shown, the charging management module also includes a charging circuit 30, which is electrically connected to the input terminal in, the battery charging / discharging terminal Vb, the system operating voltage terminal Vs, and the charging control unit 20. The charging control unit 20 is used to control the voltage conversion circuit 10 to operate in constant current (CC) charging mode, charging the battery 142 through the voltage conversion circuit 10 provided in this embodiment. The charging control unit 20 is also used to control the voltage conversion circuit 10 to be in a non-operating state and control the charging circuit 30 to provide charging voltage to the battery charging / discharging terminal Vb in constant voltage (CV) charging mode, i.e., charging the battery 142 through the charging circuit 30 in CV charging mode. In CC charging mode, the charging current is larger, and charging the battery 142 through the voltage conversion circuit 10 can reduce losses to a greater extent. In CV charging mode, the charging current is smaller, and charging the battery 142 through the charging circuit 30 allows for more stable charging voltage by utilizing the feedback regulation function in the charging circuit 30.

[0062] In one possible implementation, such as Figure 18 As shown, the charging management module also includes a charging circuit 30, which is electrically connected to the input terminal in, the battery charging / discharging terminal Vb, the system operating voltage terminal Vs, and the charging control unit 20. The charging control unit 20 is used to control the voltage conversion circuit 10 to be in working state when the charging current is greater than a preset value in constant current CC charging mode. The charging control unit 20 is also used to control the voltage conversion circuit 10 to be in non-working state when the charging current is not greater than the preset value in constant current CC charging mode and in constant voltage CV charging mode, and to control the charging circuit 30 to provide charging voltage to the battery charging / discharging terminal Vb. In CC charging mode, the charging current may still change. Therefore, the switching between the voltage conversion circuit 10 and the charging circuit 30 can be controlled solely based on the magnitude of the charging current. When the charging current is large, the battery 142 is charged through the voltage conversion circuit 10, which can reduce losses to a greater extent. When the charging current is small, the battery 142 is charged through the charging circuit 30, making the charging voltage more stable.

[0063] Additionally, it should be noted that in trickle charging mode, the voltage conversion circuit 10 can be controlled to be in a non-operating state, and the charging circuit 30 can be controlled to provide charging voltage to the battery charging / discharging terminal Vb. The charging circuit 30 may include other circuits with charging / discharging functions, such as a buck circuit, a boost circuit, or a BUCK-BOOST circuit.

[0064] In one possible implementation, such as Figure 18 As shown, the charging circuit 30 is also electrically connected to the system operating voltage terminal Vs. The charging circuit 30 is also used to provide operating voltage to the system operating voltage terminal Vs. That is, in the electronic device, there is also a system device 40 electrically connected to the system operating voltage terminal Vs, that is, the charging circuit 30 is also used to supply power to the system device 40.

[0065] like Figure 1 As shown in the illustration, this application also provides an electronic device, including the voltage conversion circuit 10 or the charging management module 140 described above. The specific structure and principle of the voltage conversion circuit 10 and the charging management module 140 are the same as in the above embodiments, and will not be repeated here. The electronic device in this application can be used in any scenario requiring voltage conversion, such as servers, data centers, DC power supplies, etc.

[0066] In this application embodiment, "at least one" refers to one or more, and "more than one" refers to two or more. "And / or" describes the relationship between related objects, indicating that three relationships can exist. For example, A and / or B can represent the existence of A alone, the simultaneous existence of A and B, or the existence of B alone. A and B can be singular or plural. The character " / " generally indicates that the preceding and following related objects are in an "or" relationship. "At least one of the following" and similar expressions refer to any combination of these items, including any combination of single or plural items. For example, at least one of a, b, and c can represent: a, b, c, ab, ac, bc, or abc, where a, b, and c can be single or multiple.

[0067] The above are merely preferred embodiments of this application and are not intended to limit this application. Various modifications and variations can be made to this application by those skilled in the art. Any modifications, equivalent substitutions, improvements, etc., made within the spirit and principles of this application should be included within the protection scope of this application.

Claims

1. A voltage conversion circuit, characterized in that, include: The first switching unit has its first terminal electrically connected to the input terminal; The second switching unit has its first terminal electrically connected to the second terminal of the first switching unit; The first capacitor unit has its first terminal electrically connected to the second terminal of the first switch unit; The second capacitor unit has its first terminal electrically connected to the second terminal of the second switch unit; The third switching unit, wherein the first end of the third switching unit is electrically connected to the second end of the first capacitor unit; The fourth switching unit has its first terminal electrically connected to the second terminal of the first capacitor unit, and its second terminal electrically connected to the ground terminal. The fifth switching unit, wherein the first end of the fifth switching unit is electrically connected to the second end of the third switching unit; The third capacitor unit, wherein the first end of the third capacitor unit is electrically connected to the second end of the third switch unit; The sixth switching unit has its first terminal electrically connected to the second terminal of the third capacitor unit, and its second terminal electrically connected to the second terminal of the fifth switching unit. The seventh switching unit has its first terminal electrically connected to the second terminal of the third capacitor unit, and its second terminal electrically connected to the ground terminal. The eighth switching unit has its first terminal electrically connected to the second terminal of the second switching unit, and its second terminal electrically connected to the output terminal. The ninth switching unit has its first terminal electrically connected to the second terminal of the second capacitor unit, and its second terminal electrically connected to the output terminal. The tenth switch unit has its first terminal electrically connected to the second terminal of the second capacitor unit, and its second terminal electrically connected to the ground terminal. When the voltage conversion circuit is in operation, it operates in multiple periodic time periods, each of which includes a first time period and a second time period in sequence. During the first time period, the first switch unit, the third switch unit, the sixth switch unit, the eighth switch unit, and the tenth switch unit are turned on, while the second switch unit, the fourth switch unit, the fifth switch unit, the seventh switch unit, and the ninth switch unit are turned off. During the second time period, the first switch unit, the third switch unit, the sixth switch unit, the eighth switch unit, and the tenth switch unit are turned off, while the second switch unit, the fourth switch unit, the fifth switch unit, the seventh switch unit, and the ninth switch unit are turned on.

2. The voltage conversion circuit according to claim 1, characterized in that, The first switch unit, the second switch unit, the third switch unit, the fourth switch unit, the fifth switch unit, the sixth switch unit, the seventh switch unit, the eighth switch unit, the ninth switch unit, and the tenth switch unit are metal-oxide-semiconductor field-effect transistors (MOSFETs), gallium nitride (GaN) transistors, silicon carbide (SiC) transistors, insulated-gate bipolar transistors (IGBTs), or relays.

3. The voltage conversion circuit according to claim 2, characterized in that, Also includes: A reverse current protection transistor is connected in series between the input terminal and the first switching unit. The parasitic diode of the reverse current protection transistor is oriented in a first direction, and the parasitic diode of the first switching unit is oriented in a second direction. The first direction is opposite to the second direction.

4. A charging management module, characterized in that, include: The voltage conversion circuit as described in any one of claims 1 to 3, wherein the output terminal of the voltage conversion circuit is electrically connected to the battery charging and discharging terminal; A charging control unit is electrically connected to the control terminal of each of the switching units in the voltage conversion circuit. The charging control unit is used to control the voltage conversion circuit to be in a working state or a non-working state.

5. The charging management module according to claim 4, characterized in that, When the voltage conversion circuit is in the non-operating state, the charging control unit is used to provide a cutoff level to the control terminals of the first switch unit, the second switch unit, the third switch unit, the fourth switch unit, the fifth switch unit, the sixth switch unit, the seventh switch unit, the eighth switch unit, the ninth switch unit, and the tenth switch unit.

6. The charging management module according to claim 4, characterized in that, Also includes: A charging circuit, wherein the charging circuit is electrically connected to the input terminal, the battery charging / discharging terminal, the system operating voltage terminal, and the charging control unit; The charging control unit is used to control the voltage conversion circuit to be in the working state in constant current charging mode. The charging control unit is also used to control the voltage conversion circuit to be in the non-working state in constant voltage charging mode and to control the charging circuit to provide charging voltage to the battery charging and discharging terminals.

7. The charging management module according to claim 4, characterized in that, Also includes: A charging circuit, wherein the charging circuit is electrically connected to the input terminal, the battery charging / discharging terminal, and the charging control unit; The charging control unit is used to control the voltage conversion circuit to be in the working state when the charging current is greater than the preset value in constant current charging mode. The charging control unit is also used to control the voltage conversion circuit to be in the non-working state when the charging current is not greater than the preset value in constant current charging mode and in constant voltage charging mode, and to control the charging circuit to provide charging voltage to the battery charging and discharging terminals.

8. The charging management module according to claim 6 or 7, characterized in that, The charging circuit is also electrically connected to the system operating voltage terminal, and the charging circuit is also used to provide operating voltage to the system operating voltage terminal.

9. An electronic device, characterized in that, It includes the voltage conversion circuit as described in any one of claims 1 to 3 or the charging management module as described in any one of claims 4 to 8.

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