A modeling method for miniaturized dual-frequency omnidirectional antenna

Abstract

The present invention discloses a miniaturized dual-frequency omnidirectional antenna and a microstrip antenna modeling method, wherein the miniaturized dual-frequency omnidirectional antenna comprises: a dielectric substrate, a radiating metal sheet on the upper layer of the dielectric substrate, a feeding point and a metal bottom plate below the dielectric substrate, wherein the radiating metal sheet comprises a feeding sheet, a coupling sheet and a short-circuit patch; the feeding point is located at the center of the feeding sheet, the feeding sheet is surrounded by the coupling sheet and the coupling sheet is coupled with the feeding sheet; the short-circuit patch is located between the coupling sheets; the short-circuit patch and the feeding sheet work together to produce a zero-order resonance characteristic; the first resonance frequency and the second resonance frequency are adjusted by adjusting the size of the short-circuit patch and the feeding sheet. The present invention solves the technical problems of large size, high profile, poor omnidirectional radiation characteristics and limited application scenarios of multi-band antennas.

Description

Technical Field

[0001] The invention belongs to the technical field of microstrip antennas, and in particular relates to a modeling method for a miniaturized dual-frequency omnidirectional antenna. Background Art

[0002] At present, omnidirectional radiating antennas can form 360° uniform signal coverage on the plane formed by the maximum antenna radiation direction and the magnetic field direction. This type of antenna has been widely used in current wireless communication networks, especially in indoor distributed systems of mobile communications. The most commonly used form is the monopole antenna, which has a simple antenna structure and a conical vertical surface. However, the height of this antenna is generally one-quarter of the wavelength, which greatly increases the height of the original carrier and is very unfavorable for use in actual products. In order to reduce the height of the antenna, a variety of design methods have been proposed. The monopole is bent into an L form or a PIFA form, which effectively reduces the height of the antenna profile, but the asymmetry of the overall structure of the antenna deteriorates the omnidirectional radiation characteristics to a certain extent.

[0003] Multi-band omnidirectional antennas are usually realized by adding parasitic units on the basis of low-frequency omnidirectional antennas. The size of this dual-band omnidirectional antenna is directly related to the size of the low-frequency antenna, which is generally a quarter of a wavelength. By adding parasitic units, not only the size of the original antenna is increased, but also the overall structure of the antenna is complicated, which is not conducive to controlling the overall size of the antenna, resulting in problems such as limited application scenarios of the antenna.

[0004] In order to effectively solve the problems of large size, high profile, poor omnidirectional radiation characteristics and limited application scenarios of multi-band antennas, a miniaturized dual-band omnidirectional antenna modeling method was proposed. Summary of the invention

[0005] The embodiments of the present invention provide a miniaturized dual-frequency omnidirectional antenna and a microstrip antenna modeling method to at least solve the problems of large size, high profile, poor omnidirectional radiation characteristics, and limited application scenarios of multi-band antennas in related technologies.

[0006] According to one embodiment of the present invention, a miniaturized dual-band omnidirectional antenna is provided, comprising a dielectric substrate, a radiating metal sheet on the upper layer of the dielectric substrate, a feeding point and a metal bottom plate below the dielectric substrate, wherein the radiating metal sheet comprises a feeding sheet, a coupling sheet and a short-circuit patch; the feeding point is located at the center of the feeding sheet, the feeding sheet is surrounded by the coupling sheet and the coupling sheet is coupled to the feeding sheet; the short-circuit patch is located between the coupling sheets; the short-circuit patch and the feeding sheet work together to produce a zero-order resonance characteristic; by adjusting the size of the short-circuit patch and the feeding sheet, the eigenmode of the radiating metal sheet can be changed, thereby adjusting its corresponding first resonant frequency and second resonant frequency.

[0007] In an exemplary embodiment, the dielectric substrate includes any one or a combination of multiple dielectrics of insulating dielectrics or air dielectrics.

[0008] In an exemplary embodiment, the outer contour shape of the radiation metal sheet is a centrally symmetrical shape, including any one or a combination of a circle, a triangle, and an equilateral polygon.

[0009] In an exemplary embodiment, the radiation metal plate includes at least one feeding plate, one coupling plate and three short-circuit patches.

[0010] In an exemplary embodiment, the shape of the feeding plate is a symmetrical shape, including any one or a combination of a circle, an ellipse, and an equilateral polygon; the feeding plate excites the TM02 mode to achieve omnidirectional radiation characteristics.

[0011] In an exemplary embodiment, the coupling plate is composed of a coupling ring surrounding the feeding plate and symmetrically distributed coupling branches; the coupling ring is used to increase the equivalent capacitance of the feeding plate; the coupling branches are used to increase the coupling capacitance between the feeding plate and the short-circuit patch, and the length of the coupling plate branches is greater than or equal to the radial length of the adjacent short-circuit patches.

[0012] In an exemplary embodiment, the short-circuit patches are distributed at equal angles between the coupling branches, and the short-circuit patches are composed of metal sheets and metal vias, and the metal vias are any one or more combinations of through holes located in the metal sheet or metal rods; the horizontal plane radiation energy in the corresponding direction is adjusted by adjusting the number of short-circuit patches.

[0013] In an exemplary embodiment, the coupling patch is kept at a distance from the feeding patch and the short-circuit patch so as not to make direct electrical contact therebetween.

[0014] In an exemplary embodiment, when the antenna operates at the first resonant frequency, the antenna operating mode is zero-order resonance, and the resonant frequency is Where L L is the inductance of the short-circuited patch, C L is the capacitance of the short-circuited patch, C C is the coupling capacitance between the feed patch and the short-circuit patch, L R is the equivalent inductance of the feed sheet, C R is the equivalent capacitance of the feed patch. The inductance L of the short-circuit patch L And the capacitor C of the short-circuit patch L Related to the size of the short-circuit patch, the equivalent inductance L of the feed patch R The capacitance C equivalent to the feed plate R Related to the size of the feed plate.

[0015] In an exemplary embodiment, when operating at the second resonant frequency, the antenna operates in the TM mode and the resonant frequency is where c 0 is the speed of light in a vacuum, ∈ r is the relative dielectric constant of the dielectric substrate, a is the radius of the feed plate, L R is the equivalent inductance of the feed sheet, C R is the equivalent capacitance of the feed plate.

[0016] In an exemplary embodiment, one end of the coaxial cable or the inner core of the connector is connected to the feeding plate through a feeding point, and the other end of the coaxial cable or the outer wall of the connector is connected to the metal bottom plate.

[0017] According to one embodiment of the present invention, a modeling method for a miniaturized dual-band omnidirectional antenna is provided, comprising the steps of:

[0018] Determine the basic model of microstrip antenna;

[0019] The basic model of the microstrip antenna is discretized. The discretization operation is to use three-dimensional high-frequency electromagnetic simulation software to divide the entire model into different grids or discrete points.

[0020] Each discrete grid or discrete point is aggregated and classified.

[0021] Simulation adjustment is to select the position of each discrete grid or discrete point according to the design goal and perform simulation verification. When the simulation results do not meet the expectations, adjust the corresponding components.

[0022] In an exemplary embodiment, the discretization operation on the microstrip antenna basic model comprises the steps of:

[0023] Calculating the functional relevance based on the functional relationship and / or parameter change correlation between different functional modules of the microstrip antenna;

[0024] Calculating the position correlation according to the distance and / or connection relationship between different functional modules of the microstrip antenna;

[0025] Calculating frequency correlation according to the influence of different functional modules of the microstrip antenna on the resonant frequency and / or the influence on the simulation results;

[0026] Calculate the correlation weights between different functional modules of the microstrip antenna according to the functional correlation and / or position correlation and / or frequency correlation between different functional modules of the microstrip antenna;

[0027] Functional modules whose correlation weights are greater than or equal to a preset correlation threshold are divided into the same grid or discrete points, and functional modules whose correlation weights are less than a preset correlation threshold are divided into different grids or discrete points, thereby realizing the discretization operation of the basic model of the microstrip antenna.

[0028] The present invention has the advantages that:

[0029] (1) The miniaturized dual-band omnidirectional antenna of the present invention uses a short-circuit patch and a feed patch to work together to produce zero-order resonance characteristics, and realizes dual-frequency antenna characteristics through parallel inductance and series capacitance. The first resonance frequency of the antenna is the zero-order resonance mode, breaking through the limitation of physical size on resonance frequency. The overall size of the antenna is small, the profile is low, and the height is much lower than the conventional 0.25λ, where λ is the free space wavelength.

[0030] (2) The miniaturized dual-band omnidirectional antenna of the present invention adopts the form of coupling rings and coupling branches, which can increase the coupling capacitance between the feed plate and the short-circuit patch, thereby effectively reducing the resonant frequency and reducing the overall size of the antenna. At the same time, the antenna can generate an equivalent annular magnetic current and reduce the overall cross-sectional height of the antenna.

[0031] (3) The miniaturized dual-band omnidirectional antenna of the present invention adopts a circular feed plate and short-circuit patches arranged at equal angles around it, which can simply and effectively realize the omnidirectional radiation characteristics of the antenna.

[0032] (4) According to the functional correlation and / or position correlation and / or frequency correlation between different functional modules of the microstrip antenna, the basic model of the microstrip antenna is discretized and machine learning is performed on it, so that the microstrip antenna model can be effectively established and quickly optimized. BRIEF DESCRIPTION OF THE DRAWINGS

[0033] Figure 1 1 is a top view of the miniaturized dual-band omnidirectional antenna of the present invention.

[0034] Figure 2 It is a side view of the miniaturized dual-band omnidirectional antenna of the present invention.

[0035] Figure 3 It is an equivalent circuit diagram of the miniaturized dual-band omnidirectional antenna of the present invention.

[0036] Figure 4 It is a scattering parameter diagram of the miniaturized dual-band omnidirectional antenna of the present invention.

[0037] Figure 5 This is the E-plane radiation pattern of the miniaturized dual-band omnidirectional antenna of the present invention.

[0038] Figure 6 This is the H-plane radiation pattern of the miniaturized dual-band omnidirectional antenna of the present invention.

[0039] Figure 7 is a flow chart of a method for improving and designing a microwave device based on machine learning according to an embodiment of the present invention;

[0040] Figure 8is a method flow chart of sub-step S02 of the method for improving and designing a microwave device based on machine learning according to an embodiment of the present invention; DETAILED DESCRIPTION

[0041] The present invention is described in detail below in conjunction with specific embodiments. The following embodiments will help those skilled in the art to further understand the invention, but are not intended to limit the present invention in any form. It should be noted that, for those of ordinary skill in the art, several changes and improvements can be made without departing from the concept of the present invention. These all belong to the protection scope of the present invention.

[0042] A miniaturized dual-band omnidirectional antenna according to an embodiment of the present invention, the top view of which is shown in FIG. Figure 1 As shown, the side view is Figure 2 As shown, it comprises a dielectric substrate (2), a radiating metal sheet (1) on the upper layer of the dielectric substrate, a feeding point (4) and a metal bottom plate below the dielectric substrate, wherein the radiating metal sheet comprises a feeding sheet (3), a coupling sheet (9) and a short-circuit patch (5); the feeding point (4) is located at the center of the feeding sheet, the feeding sheet (3) is surrounded by the coupling sheet (9) and the coupling sheet is coupled to the feeding sheet; the short-circuit patch (5) is located between the coupling sheets (9); the short-circuit patch (5) and the feeding sheet (3) work together to generate a zero-order resonance characteristic; and the first resonance frequency and the second resonance frequency are adjusted by changing the sizes of the short-circuit patch and the feeding sheet.

[0043] In a preferred embodiment, the dielectric substrate (2) includes any one or more combinations of insulating media or air media. In this embodiment, according to the application scenario and design requirements of the antenna, the dielectric substrate can use an insulating medium, such as a glass fiber reinforced polytetrafluoroethylene resin series, a ceramic powder filled polytetrafluoroethylene resin series, a ceramic powder filled thermosetting resin series, an epoxy board, etc.; air can also be used as a medium, that is, air is used as a filler between the radiating metal sheet and the metal base plate; a mixed medium of insulating media and air can also be used. The relative dielectric constants of different dielectric substrates ∈ r The thickness of the dielectric substrate has a certain influence on the working bandwidth of the antenna, which is generally between 0.2mm and 6mm.

[0044] In a preferred embodiment, the outer contour shape of the radiating metal sheet is a centrally symmetrical shape, including any one or a combination of a circle, a triangle, and an equilateral polygon. In this embodiment, the outer contour shape of the radiating metal sheet is related to the application scenario and design requirements of the antenna. The outer contour of the radiating metal sheet has a certain influence on the fluctuation of the horizontal plane radiation pattern. By adjusting the shape contour of the radiating metal sheet, the radiation in the local direction can be strengthened or weakened. The outer contour of the radiating metal sheet includes centrally symmetrical shapes such as a circle, a triangle, and an equilateral polygon. In another preferred embodiment, the inside of the radiating metal sheet can be grooved.

[0045] In a preferred embodiment, the radiation metal sheet includes at least one feeding sheet, one coupling sheet and three short-circuit patches. Figure 1 and Figure 2 In a preferred embodiment shown, the radiating metal sheet includes 1 feeding sheet (3), 1 coupling sheet (9) and 12 short-circuit patches (5). The number of short-circuit patches can be adjusted according to the application scenario and design requirements of the antenna. The more short-circuit patches there are, the smaller the fluctuation of the omnidirectional radiation performance of the directional pattern of the first resonant frequency. According to different application scenarios and design requirements, the number of short-circuit patches can be increased or decreased in a specific direction, thereby enhancing or weakening the horizontal plane radiation energy in this direction.

[0046] In a preferred embodiment, the shape of the feed plate is symmetrical, including any one or a combination of a circle, an ellipse, and an equilateral polygon. The shape of the feed plate is consistent with the outer contour of the radiation metal plate, thereby ensuring the consistency of the radiation characteristics at the two resonant frequencies. Figure 1 and Figure 2 In a preferred embodiment shown, the shape of the feed plate (3) is circular. Generally, the size of the dielectric substrate (2) is Φ70×1.5 mm, and the maximum size of the radiation metal patch is Φ50 mm.

[0047] When an electromagnetic signal is fed into the circular feed plate (3) from the feed point (4), the TM02 mode can be excited. At this time, the electric field is located between the feed plate (3) and the metal base plate, and the electric field is There is no change in direction. The electric field around the feed plate can be equivalent to a circular magnetic current, thus achieving the characteristic of omnidirectional radiation.

[0048] In a preferred embodiment, the coupling plate is composed of a coupling ring surrounding the feed plate and symmetrically distributed coupling branches; the coupling ring is used to increase the equivalent capacitance of the feed plate; the coupling branches are used to increase the coupling capacitance between the feed plate and the short-circuit patch, and the length of the coupling plate branch is not less than the radial length of the adjacent short-circuit patch. Figure 1 and Figure 2 In a preferred embodiment shown, the coupling plate (9) includes a coupling branch (91) and a coupling ring (92). Since the feed plate (3) is circular, the coupling ring (92) is a coupling circular ring surrounding the feed plate. The coupling ring (92) loads the feed plate (3) to increase the equivalent capacitance of the feed plate. The coupling branch (91) increases the coupling capacitance between the feed plate (3) and the short-circuit patch (5). Therefore, the size and position of the coupling plate can affect the parallel capacitance C R And the series capacitor C L , thereby reducing the corresponding operating frequency and realizing the miniaturization design of the antenna.

[0049] In a preferred embodiment, the short-circuit patches are distributed between the coupling branches at equal angles, and the short-circuit patches are composed of metal sheets and metal vias, and the metal vias are any one or a combination of through holes located in the metal sheet or metal thin rods. Figure 1 and Figure 2 In a preferred embodiment shown, the short-circuit patch (5) is composed of a fan-shaped metal sheet and a metal via (6), and the metal via (6) can be realized in the form of a through hole or a metal thin rod. As a further optimization scheme of the embodiment of the present invention, the metal via (6) is located at the center of the short-circuit patch (5), so that the current distribution on the short-circuit patch is more uniform, and the inductance characteristics formed by the short circuit are more stable, avoiding the edge effect caused by the edge of the short-circuit patch. The short-circuit patches are arranged at equal angles between the coupling branches and work together with the feed sheet to produce zero-order resonance characteristics. This zero-order resonance mode is related to the position and size of the short-circuit patch, and its horizontal plane directional pattern characteristics are affected by the number and arrangement of the short-circuit patches. The equal-angle spacing arrangement can form an omnidirectional radiation characteristic with small fluctuations in the horizontal plane directional pattern.

[0050] In a preferred embodiment, the coupling plate (9) maintains a distance from the feeding plate (3) and the short-circuit patch (5) so as not to be in direct electrical contact. Figure 1 and Figure 2 In a preferred embodiment shown, the coupling plate (9) maintains a certain distance from the feeding plate (3) and the short-circuit patch (5), generally between 0.1 mm and 3 mm.

[0051] In a preferred embodiment, the first resonant frequency and the second resonant frequency are adjusted by changing the sizes of the short-circuit patch and the feed patch, and the adjustment principle is:

[0052] When the antenna operates at the first resonant frequency, the antenna operating mode is zero-order resonance, and the resonant frequency is Where L L is the inductance of the short-circuited patch, C L is the capacitance of the short-circuited patch, C C is the coupling capacitance between the feed patch and the short-circuit patch, L R is the equivalent inductance of the feed sheet, C R is the equivalent capacitance of the feed patch. The inductance L of the short-circuit patch L And the capacitor C of the short-circuit patch L Related to the size of the short-circuit patch, the equivalent inductance L of the feed patch R The capacitance C equivalent to the feed plate R Related to the size of the feed plate.

[0053] When working at the second resonant frequency, the working mode of the antenna is TM mode, and the resonant frequency is where c 0 is the speed of light in a vacuum, ∈ r is the relative dielectric constant of the dielectric substrate, a is the radius of the feed plate, L R is the equivalent inductance of the feed sheet, C R is the equivalent capacitance of the feed plate.

[0054] The inductance L of the short-circuit patch can be adjusted by changing the size of the short-circuit patch. L And the capacitor C of the short-circuit patch L By changing the size of the feed sheet, the equivalent inductance L of the feed sheet can be adjusted. R The capacitance C equivalent to the feed plate R , so the first resonant frequency f can be effectively adjusted according to the above formula 1 and the second resonant frequency f 2 .

[0055] The equivalent circuit diagram of the miniaturized dual-band omnidirectional antenna of the preferred embodiment of the present invention is as follows: Figure 3 As shown, the equivalent circuit structure of the antenna is equivalent to a composite left-handed transmission line. The circular feed plate (3) is equivalent to a series inductor L R And the parallel capacitor C R , determines the right-hand component of the transmission line; the short-circuit patch (5) is equivalent to the series capacitor C L And the parallel inductor L L , determines the left-hand component of the transmission line; the size and position of the coupling plate (9) can affect the parallel capacitance and the series capacitance, thereby reducing the corresponding operating frequency. According to the composite left-handed transmission line theory, the antenna can have a zero electromagnetic wave propagation constant at a certain frequency, so that the antenna resonant frequency is not limited by the physical size, that is, the model zero-order resonance. When the antenna works in the zero-order resonance mode, the feed plate (3) is equivalent to a series inductor and a parallel capacitor, and the short-circuit patch (5) is equivalent to a series capacitor and a parallel inductor. The coupling plate (9) can effectively increase the coupling capacitance value C between the short-circuit patch and the feed plate. C .

[0056] In a preferred embodiment, one end of the coaxial cable or the inner core of the connector is connected to the feeding plate through the feeding point, and the other end of the coaxial cable or the outer wall of the connector is connected to the metal bottom plate. Figure 2 As shown, the feeding point (4) of the antenna is located at the center of the feeding plate (3), the inner core (7) of the coaxial cable (8) or the connector is connected to the feeding plate (3) through a via hole, and the outer wall of the coaxial cable (8) or the connector is connected to the metal floor below the dielectric substrate (2). Electromagnetic wave signals can be fed into the feeding plate (3) of the antenna.

[0057] In a preferred embodiment, the characteristic impedance of the connector or cable connected to the feeding point (4) is 50Ω.

[0058] The scattering parameter diagram of the miniaturized dual-band omnidirectional antenna of the preferred embodiment of the present invention is as follows: Figure 4 As shown, the horizontal axis is frequency (GHz) and the vertical axis is decibel value (dB). The antenna can resonate at two frequencies, 1.9 GHz and 2.75 GHz, thereby achieving dual-band working characteristics.

[0059] The vertical plane radiation pattern of the miniaturized dual-band omnidirectional antenna at the resonant frequency of the preferred embodiment of the present invention is as follows: Figure 5 As shown, its vertical radiation pattern is similar to that of a monopole antenna, both of which are conical in shape and have a null greater than 30 dB on the wide side, thereby avoiding concentrated radiation on the ultra-wide side of the antenna and radiating evenly in all directions.

[0060] The horizontal plane radiation pattern of the miniaturized dual-band omnidirectional antenna at the resonant frequency of the preferred embodiment of the present invention is as follows: Figure 6 As shown in the figure, the horizontal radiation pattern has a gain fluctuation of less than 3dB within the range of 360°. Therefore, the horizontal coverage of the antenna is circular, that is, the horizontal radiation is omnidirectional.

[0061] The miniaturized dual-band omnidirectional antenna of the preferred embodiment of the present invention can work in the zero-order resonant mode and the TM02 mode at the same time, and both have a radiation pattern similar to that of a monopole antenna.

[0062] In another preferred embodiment, the miniaturized dual-band omnidirectional antenna of the present invention can change the two operating frequencies of the antenna by changing the corresponding parameters of the structure. By adjusting the dielectric constant and substrate thickness of the dielectric substrate, the size of the two resonant frequencies can be adjusted simultaneously. By changing the size of the short-circuit patch and the feed patch, the corresponding first resonant frequency and the second resonant frequency can be adjusted separately. By adjusting the size and shape of the coupling patch, the corresponding fusion coupling can be increased, the resonant frequency can be reduced, and the antenna working bandwidth can be affected to a certain extent.

[0063] As an embodiment, a microstrip antenna modeling method, the flow chart is as follows Figure 7 As shown, the steps include:

[0064] Step S01, determine the basic model of the antenna. In this embodiment, a dielectric substrate (2) and a metal base plate are established, and a corresponding radiation circuit is established on the other side of the dielectric substrate, including a basic model of a microstrip antenna including a circular feeding plate (3), a short-circuit patch (5), a coupling plate (9), and corresponding feeding points (4) and a short-circuit through hole.

[0065] Step S02: discretize the basic model of the microstrip antenna. The discretization operation is to use three-dimensional high-frequency electromagnetic simulation software to divide the entire model into different grids or discrete points.

[0066] Step S03: Aggregate and classify each discrete grid or discrete point. For example, a KNN (K-Nearest Neighbor) nearest neighbor classification algorithm is used to aggregate and classify each discrete grid or discrete point.

[0067] Step S04, simulation adjustment, that is, selecting the position of each discrete grid or discrete point according to the design goal and performing simulation verification, and adjusting the corresponding components when the simulation results do not meet expectations. In this embodiment, the position of each discrete grid or discrete point is selected according to the design goal and simulation verification is performed. When the simulation results do not meet expectations, the first resonant frequency is adjusted. and the second resonant frequency The formula is adjusted for the corresponding capacitance and inductance.

[0068] In a preferred embodiment, the sub-step S02 is as shown in the flow chart: Figure 8 As shown, the steps include:

[0069] Step S021, calculating the functional correlation according to the functional relationship and / or parameter change correlation between different functional modules of the microstrip antenna;

[0070] Step S022, calculating the position correlation according to the distance and / or connection relationship between different functional modules of the microstrip antenna;

[0071] Step S023, calculating the frequency correlation according to the influence degree of different functional modules of the microstrip antenna on the resonant frequency and / or the influence degree on the simulation result;

[0072] Step S024, calculating the correlation weights between different functional modules of the microstrip antenna according to the functional correlation and / or position correlation and / or frequency correlation between different functional modules of the microstrip antenna;

[0073] Step S025, divide the functional modules whose correlation weights are greater than or equal to the preset correlation threshold into the same grid or discrete points, and split the functional modules whose correlation weights are less than the preset correlation threshold into different grids or discrete points, so as to realize the discretization operation of the basic model of the microstrip antenna.

[0074] In this embodiment, the function correlation is calculated according to the function relationship and / or parameter change correlation between different function modules of the microstrip antenna, which is: calculating the function correlation according to the positive correlation between the function influence degree and the function correlation between different function modules of the microstrip antenna, calculating the function correlation according to the positive correlation between the parameter change correlation and the function correlation between different function modules of the microstrip antenna, or calculating the function correlation according to the positive correlation between the function influence degree and the parameter change correlation and the function correlation between different function modules of the microstrip antenna, which is represented by a variable p;

[0075] The calculating of the position correlation according to the distance and / or connection relationship between different functional modules of the microstrip antenna is: calculating the position correlation according to the positive correlation between the distance and the position correlation between different functional modules of the microstrip antenna, calculating the position correlation according to the positive correlation between the connectivity (connectivity is set according to whether there is a connection) and the position correlation between different functional modules of the microstrip antenna, and calculating any one of the position correlation according to the positive correlation between the distance and connectivity and the position correlation between different functional modules of the microstrip antenna, represented by the variable q;

[0076] The frequency correlation is calculated according to the influence degree of different functional modules of the microstrip antenna on the resonant frequency and / or the influence degree on the simulation result, which is: calculating the frequency correlation according to the positive correlation between the influence degree of different functional modules of the microstrip antenna on the resonant frequency and the frequency correlation, calculating the frequency correlation according to the positive correlation between the influence degree of different functional modules of the microstrip antenna on the simulation result and the frequency correlation, or calculating the frequency correlation according to the positive correlation between the influence degree of different functional modules of the microstrip antenna on the resonant frequency and the influence degree on the simulation result and the frequency correlation, and any one of the above is represented by the variable w.

[0077] The method of calculating the correlation weights between different functional modules of the microstrip antenna according to the functional correlation and / or position correlation and / or frequency correlation between different functional modules of the microstrip antenna comprises: calculating the correlation weights between different functional modules of the microstrip antenna according to the positive correlation between the functional correlation and the correlation weights between different functional modules of the microstrip antenna, calculating the correlation weights between different functional modules of the microstrip antenna according to the positive correlation between the position correlation and the correlation weights between different functional modules of the microstrip antenna, calculating the correlation weights between different functional modules of the microstrip antenna according to the positive correlation between the frequency correlation and the correlation weights between different functional modules of the microstrip antenna, and calculating the correlation weights between different functional modules of the microstrip antenna according to the positive correlation between the functional correlation and the position correlation between different functional modules of the microstrip antenna. The correlation weights between different functional modules of the microstrip antenna are calculated according to the positive correlation between the functional correlation and the correlation weight, the correlation weights between different functional modules of the microstrip antenna are calculated according to the positive correlation between the functional correlation and the frequency correlation and the correlation weight, the correlation weights between different functional modules of the microstrip antenna are calculated according to the positive correlation between the position correlation and the frequency correlation and the correlation weight, and any one of the correlation weights between different functional modules of the microstrip antenna is calculated according to the positive correlation between the functional correlation and the position correlation and the frequency correlation and the correlation weight, and the correlation weights between different functional modules of the microstrip antenna are represented by the variable z.

[0078] A1 to A7 in Table A represent different implementation methods for calculating relevant weights, wherein the functional relevance p, position relevance q, and frequency relevance w involved in Table A are obtained using the formulas in the above implementation methods.

[0079] Table A Different ways to calculate the relevant weights

[0080]

[0081]

[0082]

[0083]

[0084]

[0085]

[0086]

[0087]

[0088]

[0089]

[0090]

[0091]

[0092]

[0093]

[0094]

[0095]

[0096]

[0097]

[0098]

[0099]

[0100]

[0101]

[0102]

[0103]

[0104]

[0105]

[0106]

[0107]

[0108]

[0109]

[0110]

[0111]

[0112]

[0113]

[0114] In this embodiment, the pre-set relevant threshold Z = 0.8, and the relevant weights between different modules are calculated according to the method described in any item in Table A. For example, if the relevant weight between two certain modules is 0.81 > Z, then these two functional modules are divided into the same grid or discrete points. If the relevant weight between two modules is 0.78 < Z, then the functional modules with relevant weights less than the pre-set relevant threshold are split into different grids or discrete points. The above steps are performed on all functional modules to achieve the discretization operation of the basic model of the microstrip antenna.

[0115] Of course, those of ordinary skill in the art should recognize that the above embodiments are only used to illustrate the present invention and are not intended to limit the present invention. As long as it is within the scope of the present invention, changes and modifications to the above embodiments will fall within the protection scope of the present invention.

Claims

1. A miniaturized dual-frequency omnidirectional antenna modeling method, characterized in that: Includes steps: Determine a basic model of a microstrip antenna; the basic model of the microstrip antenna includes: establishing a dielectric substrate and a metal base plate, and establishing a corresponding radiation circuit on the other side of the dielectric substrate, wherein the radiation circuit includes a circular feeding plate, a short-circuit patch, a coupling plate, and a corresponding feeding point and a short-circuit through hole of the microstrip antenna basic model; Discretization operation is performed on the basic model of the microstrip antenna; the discretization operation on the basic model of the microstrip antenna includes: calculating the functional correlation according to the functional relationship and / or parameter change correlation between different functional modules of the microstrip antenna; calculating the position correlation according to the distance and / or connection relationship between different functional modules of the microstrip antenna; calculating the frequency correlation according to the influence degree of different functional modules of the microstrip antenna on the resonant frequency and / or the influence degree on the simulation result; calculating the correlation weight between different functional modules of the microstrip antenna according to the functional correlation and / or position correlation and / or frequency correlation between different functional modules of the microstrip antenna; dividing the functional modules whose correlation weight is greater than or equal to a preset correlation threshold into the same grid or discrete points, and splitting the functional modules whose correlation weight is less than the preset correlation threshold into different grids or discrete points, so as to realize the discretization operation on the basic model of the microstrip antenna; Aggregate and classify each discrete grid or discrete point; Select the position of each discrete grid or discrete point according to the design goal and perform simulation verification. When the simulation result does not meet the expectation, adjust the corresponding capacitance and inductance according to the first resonant frequency formula and the second resonant frequency formula; The first resonant frequency formula is: Where L L is the inductance of the short-circuited patch, C L is the capacitance of the short-circuited patch, C C is the coupling capacitance between the feed patch and the short-circuit patch, L R is the equivalent inductance of the feed sheet, C R is the equivalent capacitance of the feed sheet; The second resonant frequency formula is: where c0 is the speed of light in vacuum, ∈ r is the relative dielectric constant of the dielectric substrate, a is the radius of the feed plate, L R is the equivalent inductance of the feed sheet, C R is the equivalent capacitance of the feed plate.

2. The miniaturized dual-frequency omnidirectional antenna modeling method according to claim 1, characterized in that: The dielectric substrate includes any one or a combination of multiple dielectrics such as insulating dielectrics and air dielectrics.

3. The miniaturized dual-frequency omnidirectional antenna modeling method according to claim 1, characterized in that: The circular feeding plate excites the TM02 mode to achieve omnidirectional radiation characteristics.

4. The miniaturized dual-frequency omnidirectional antenna modeling method according to claim 1, characterized in that: The coupling plate is composed of a coupling ring surrounding a circular feed plate and symmetrically distributed coupling branches; the coupling ring is used to increase the equivalent capacitance of the circular feed plate; the coupling branches are used to increase the coupling capacitance between the circular feed plate and the short-circuit patch, and the length of the coupling plate branches is greater than or equal to the radial length of the adjacent short-circuit patches.

5. The miniaturized dual-frequency omnidirectional antenna modeling method according to claim 4, characterized in that: The short-circuit patches are distributed at equal angles between the coupling branches, and the short-circuit patches are composed of metal sheets and short-circuit through holes, and the short-circuit through holes are any one or more combinations of through holes located in the metal sheets or thin metal rods; the horizontal plane radiation energy in the corresponding direction is adjusted by adjusting the number of short-circuit patches; the coupling sheet is kept at a distance from the circular feeding sheet and the short-circuit patch so as not to make direct electrical contact.

6. The miniaturized dual-frequency omnidirectional antenna modeling method according to claim 1, characterized in that: The adjustment of the corresponding capacitance and inductance according to the first resonant frequency formula and the second resonant frequency formula is to adjust the inductance L of the short-circuit patch by changing the size of the short-circuit patch. L And the capacitor C of the short-circuit patch L , by changing the size of the feed sheet, the equivalent inductance L of the feed sheet can be adjusted R The capacitance C equivalent to the feed plate R , thereby adjusting the first resonant frequency f1 and the second resonant frequency f2 according to the first resonant frequency formula and the second resonant frequency formula.

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