A phase-shift interleaved power superposition + magnetic integrated inverter topology

Abstract

The application provides a phase-shift interleaved power superposition + magnetic integrated inverter topology structure, which comprises interleaved high-frequency power switch tubes, power coupling elements, complementary low-frequency power switch tubes and filter elements; the power coupling elements comprise coupling inductors with nonlinear characteristics; the interleaved high-frequency power switch tubes, the complementary low-frequency power switch tubes and the integrated power coupling elements form a single-module coupled or multi-module coupled inverter topology structure; each switch tube in the single-module coupled inverter topology structure is in an interleaved working condition, and each inverter bridge in the multi-module coupled inverter topology structure works in a phase-shift superposition condition; the nonlinear characteristics of the coupling inductors are used to increase static inductance and reduce dynamic inductance, so as to optimize the static and dynamic natural characteristics of the inverter; the modular power superposition of the inverter is realized through phase-shift superposition; the power superposition is realized through interleaved control; the power expansion is realized through module superposition and interleaved control, and the development cost is reduced.

Description

Technical Field

[0001] This invention relates to the field of power electronics technology, and in particular to an inverter topology structure of phase-shifted interleaved power superposition + magnetic integration. Background Technology

[0002] Inverters with a wide input voltage range face several challenges. For example, a mobile vehicle's power take-off (PTO) system typically obtains mechanical power through a coupling or pulley. Because the vehicle's rotational speed varies greatly during operation, the voltage of the shaft-driven generator also varies significantly, resulting in a wide input voltage range for the inverter. These inverters have the following characteristics:

[0003] 1) The input voltage range has been widened. According to the existing standard, the DC input range is 327V to 750V.

[0004] 2) High requirements for static and dynamic characteristics, such as 100% P0 to 0 switching, voltage overshoot (drop) amplitude ≤ 5% V0 (V0 is the output voltage).

[0005] 3) High power density and small size and weight.

[0006] 4) There are many power series options, such as 1kW, 2kW, 3kW, 6kW, 12kW, etc.

[0007] These special requirements present some difficulties for the development of this type of inverter, mainly in the following aspects:

[0008] 1) The excessively wide input voltage range results in a wide variation range of the inverter modulation ratio (m = 0.43 to 0.86), which makes the design of the output filter inductor difficult;

[0009] 2) Excessive filter inductance increases the overall size and weight of the device;

[0010] 3) Excessive filter inductance degrades the dynamic characteristics of the system;

[0011] 4) Too many product varieties in the series increased research and development costs.

[0012] The existing technology and its problems are as follows: The existing technology adopts a conventional single-phase inverter scheme with a fixed L... f C fThe design and control modes include unipolar, bipolar, and unipolar frequency multiplication; control schemes include voltage, current, single-loop voltage, and hysteresis tracking. These schemes are feasible for inverters with a narrow input voltage range. However, they are not suitable for inverters with a wide input voltage range, high dynamic characteristics, and small size and weight. The core issue is the poor suitability of the output filter inductor. For inverters, their static and dynamic characteristics naturally depend on electrical parameters; a larger inductance results in better static characteristics, and a smaller inductance results in better dynamic characteristics. Therefore, a linearly constant output filter inductor is insufficient to meet the requirements.

[0013] With current technology, there are a variety of inverter models and power ratings. If a set of parameters is designed for each product, the development cost will be high, which is not conducive to inverter combination and integration. Summary of the Invention

[0014] This invention proposes an inverter topology of phase-shifted interleaved power superposition + magnetic integration, and proposes an interleaved superposition inverter technology solution. Through interleaved control, power superposition is achieved. Based on the basic model (when the inverter topology is a single-module coupled structure), the power is expanded through module superposition and interleaved control, thereby reducing the development cost.

[0015] The present invention adopts the following technical solution.

[0016] An inverter topology with phase-shifted interleaved power superposition and magnetic integration is disclosed. The inverter topology includes interleaved high-frequency power switches, power coupling elements, complementary low-frequency power switches, and filter elements. The power coupling elements include coupled inductors with nonlinear characteristics.

[0017] The interleaved high-frequency power switches, complementary low-frequency power switches, and integrated power coupling elements form a single-module coupled or multi-module coupled inverter topology. In the single-module coupled inverter topology, each switch operates in an interleaved mode, while in the multi-module coupled inverter topology, each inverter bridge operates in a phase-shifting superposition mode. By increasing the static inductance and reducing the dynamic inductance through the nonlinear characteristics of the coupled inductor, the static and dynamic natural characteristics of the inverter are optimized. The modular power superposition of the inverter is achieved through phase-shifting superposition.

[0018] When the inverter topology is a single-module coupled structure, the interleaved high-frequency power switch is the interleaved high-frequency power switch within a single module, and the power coupling element is the power coupling element within a single module; the interleaved high-frequency power switch T 11 ~T 14 Together with complementary low-frequency power switches T5-T6, they form an inverter bridge, with switch T... 11 ~T 14This is a high-frequency switch with bidirectional current flow and a 180-degree phase difference, where switching transistors T5 and T6 are low-frequency switches with a modulation wave frequency. 11 T 13 The drain of T5 and the input voltage V dc The positive terminals are connected, T 12 T 14 The source of T6 and the input voltage V dc The negative terminals are connected, T 11 The source and T 12 The drain terminals are connected to form the midpoint a of the bridge arm; T 13 The source and T 14 The drains of T5 and T6 are connected to form the midpoint b of the bridge arm; the source of T5 and the drain of T6 are connected to form the midpoint c of the bridge arm; point a is connected to the inductor L. 11 One end is connected, and point b is connected to inductor L. 12 One end is connected, L 11 With L 12 The other end is connected in parallel to form node d, L 11 L 12 Reverse coupling; node d is connected to one end of the output filter capacitor C0 to form the inverter output terminal "+", and the other end of C0 is connected to point c to form the other output terminal "-", and the output load R L Connect in parallel with the positive and negative terminals of the output;

[0019] In a single-module coupled inverter topology, the interleaved high-frequency power switch T 11 T 12 With T 13 T 14 They are 180° apart in timing, meaning they work in staggered phases, 180° apart.

[0020] When the inverter topology is a multi-module coupled structure, the interleaved high-frequency power switch is the interleaved high-frequency power switch within the multi-module, and the power coupling element is the power coupling element within the multi-module; the interleaved high-frequency power switch T 11 ~T 14 T i1 ~T i4 (i = 2, 3, ..., n) and the complementary low-frequency power switches T5 to T6 form multiple inverter bridges, with multiple modules interleaved with high-frequency power switches T i1 T i2 With T i3 T i4 A 180° phase shift, i.e., interleaved operation, reduces the phase shift angle between the inverter bridges of adjacent modules. n represents the total number of high-frequency switching modules, i.e., phase-shifted superposition.

[0021] Modular power superposition of inverters is achieved through phase-shift superposition. Specifically, to increase power, a high-frequency switching module T is added. i1 ~T i4 (i = 2, 3, ..., n); Increase the phase shift between adjacent modules, that is, the phase shift angle between inverter bridges. n represents the total number of high-frequency switching modules, which means that the inverter modules are superimposed by phase shifting, and the power is expanded by interleaving control.

[0022] The coupling inductors of a single module adopt a reverse coupling method, and their coupling coefficient K = 0.1 to 0.9.

[0023] The coupling methods of the coupled inductor include loose coupling, loose-tight coupling, and distributed coupling structures.

[0024] Both the interleaved high-frequency power switch and the complementary low-frequency power switch are SiCMOS transistors.

[0025] The filtering element is an output filtering inductor, and its design formula is as follows:

[0026]

[0027] In the formula: L f —Filter inductor (H); V0 —Output voltage (V); f s —Switching frequency (Hz); D kmin —Minimum duty cycle at the highest voltage; ΔI —Inductor current ripple, ΔI=0.4I0;

[0028] The formula for calculating the core area of ​​an inverter is:

[0029]

[0030] In the formula: A P — Area of ​​the magnetic core (cm²) 2 );I pk — Peak current (A); B — Magnetic flux density (T); J — Current carrying capacity of conductor (A / cm³) 2 ); K n —Window utilization rate, ranging from 0.3 to 0.5; where L f The larger the core area, the larger the inverter core area, which means the heavier the inverter.

[0031] The inverter topology reduces the inverter's weight by decreasing the output filter inductance. Specifically, it employs an integrated coupled inductor topology based on interleaved superposition, utilizing the nonlinear characteristics of the coupled inductors to increase the static inductance and reduce the dynamic inductance, thereby enhancing the inverter's static and dynamic natural characteristics. The coupled inductors are two-way, and their static inductance is calculated using the following formula:

[0032]

[0033]

[0034] The sum of the static inductances during one switching cycle is:

[0035]

[0036] The dynamic inductance is:

[0037] L 动 = (1-K)L Formula Six;

[0038] Formulas three, four, five, and six,

[0039] D k —Duty cycle of the Kth pulse; D′ k ——1-D k L—Self-inductance, L i (i = 1, 2) — Self-inductance of the two inductors; K — Coupling coefficient (L1=L2=L); M sensitivity;

[0040] From formulas three, four, and five, it can be seen that the static inductance after coupling is greater than that of the discrete inductor, and the inductance is related to the duty cycle. When D = 0.5, the static inductance is minimized, and the calculation formula is as follows:

[0041] L 静min =2(1+K)L(K>0) Formula 7.

[0042] The inverter is a single-phase inverter with a wide input voltage range;

[0043] Its modulated wave u(t) = U m During the positive half-cycle of sinω0t; T6 is normally on, T5 is off; one switching cycle T consists of two sawtooth wave cycles. S (f s The period of the carrier sawtooth wave During the positive half-week, T 12 T 14 Turn off, T 11 T 13 With T L It operates with alternating switching cycles;

[0044] During the period from t0 to t1, T 11 T6 is on, T 12 T 13 T 14 T5 off, V dc Through T 11 L 11C0 and T6 form a loop, V dc Power is supplied to the load; at the same time, T 14 junction diodes VD4 and L 12 C0 and T6 form a freewheeling loop for the i2(+) current.

[0045] During the period t1 to t2, T 11 T 12 T 13 T 14 When T5 is off and T6 is on, the i2(+) freewheeling circuit operates in the same manner as t0 to t1. 12 junction diodes VD2 and L 11 C0 and T6 form a freewheeling loop for the i1(+) current.

[0046] During the period from t2 to t3, T 13 T6 is on, T 11 T 12 T 14 T5 off, V dc Through T 13 L 12 C0 and T6 form a loop, V dc Power is supplied to the load; the i2(+) freewheeling circuit is the same as the process from t1 to t2. The working process from t3 to t4 is the same as the working process from t1 to t2.

[0047] During the operating periods t0~t1 and t2~t3, the coupling inductance L 11 L 12 As a static inductor, according to formulas three, four, and five, its static inductance L is... 静 Larger than discrete inductors (L 11 +L 12 );

[0048] During the operating periods t1~t2 and t3~t4, the coupling inductance L 11 L 12 As a dynamic inductor, according to Formula 6, its dynamic inductance L 动 Smaller than discrete inductor L 11 L 12 .

[0049] In summary, the advantages of this invention are: by interleaving and paralleling, the power capacity is expanded, the repetitive development of homogeneous products with different power is reduced, and the development cycle and development cost are lowered; by integrated coupling, the number, volume and weight of the inverter's magnetic components are reduced.

[0050] Compared with the prior art, the beneficial effects of the present invention are as follows:

[0051] 1) For inverters with a wide input voltage range, an inverter topology with a nonlinear coupling inductor is proposed to meet the static and dynamic requirements of the output voltage within a wide adjustment range.

[0052] 2) To address the issues of numerous power models, limited versatility, and long development cycles in this type of product, a "phase-shifting interleaved superposition" technical solution is proposed, which enables modular power superposition of inverters.

[0053] To achieve the above objectives, the basic inverter topology proposed in this invention comprises two parts: T 11 ~T 14 For interleaved high-frequency switches, T5 and T6 are complementary low-frequency switches (modulation wave frequency), T 11 T 12 With T 13 T 14 They are 180° apart in timing, i.e., interleaved; their interconnection relationship is shown in [reference needed]. Figure 1 . Figure 2 It is a multi-module coupled and integrated inverter topology that achieves power superposition, where T i1 T i2 With T i3 T i4 (i = 2, 3, ..., n) are 180° apart, i.e., they work in an interleaved manner; the phase shift angle between adjacent modules (bridge to bridge) (n is the total number of high-frequency switching modules), i.e., phase shift superposition.

[0054] By utilizing the nonlinear characteristic that the static value of the coupled inductor changes with the duty cycle (D) or the input voltage, the static and dynamic characteristics of the power supply output over a wide input voltage range can be met.

[0055] This invention also proposes coupled inductor structure methods, including distributed, loosely coupled, and loosely-tightly coupled methods. Attached Figure Description

[0056] The present invention will be further described in detail below with reference to the accompanying drawings and specific embodiments:

[0057] Appendix Figure 1 This is a schematic diagram of a single-module coupled inverter topology;

[0058] Appendix Figure 2 This is a schematic diagram of a multi-module coupled and integrated inverter topology;

[0059] Appendix Figure 3 This is a schematic diagram of an inductive coupling structure;

[0060] Appendix Figure 4 This is a schematic diagram of the control waveforms for a single-module coupled inverter topology;

[0061] Appendix Figure 5 This is a schematic diagram of the inverter topology used for simulation.

[0062] Appendix Figure 6 This is a schematic diagram of the theoretical waveform of the inverter inductor current;

[0063] Appendix Figure 7 This is a schematic diagram of the simulated waveforms of inductor current and bridge arm voltage;

[0064] Appendix Figure 8 This is a schematic diagram of the simulation waveform after the bridge arm voltage is filtered;

[0065] Appendix Figure 9 This is a schematic diagram of the inverter's output voltage and current;

[0066] Figure 1 Chinese: 1-T 11 SiCMOS transistor; 2-T 12 SiCMOS transistor; 3-T 13 SiCMOS transistor; 4-T 14 SiCMOS transistor; 5-L 12 Inductance; 6-L 11 Inductor; 7-T6SiCMOS transistor; 8-T5SiCMOS transistor; 9-R L Load; 10-C0 filter capacitor;

[0067] Figure 2 Chinese: 12-T i1 SiCMOS transistor; 13-T i2 SiCMOS transistor; 14-T i3 SiCMOS transistor; 15-T i4 SiCMOS transistor; 16-L i1 Inductor; 17-L i2 inductance. Detailed Implementation

[0068] As shown in the figure, an inverter topology with phase-shifted interleaved power superposition and magnetic integration is presented. The inverter topology includes interleaved high-frequency power switches, power coupling elements, complementary low-frequency power switches, and filter elements. The power coupling elements include coupled inductors with nonlinear characteristics.

[0069] The interleaved high-frequency power switches, complementary low-frequency power switches, and integrated power coupling elements form a single-module coupled or multi-module coupled inverter topology. In the single-module coupled inverter topology, each switch operates in an interleaved mode, while in the multi-module coupled inverter topology, each inverter bridge operates in a phase-shifting superposition mode. By increasing the static inductance and reducing the dynamic inductance through the nonlinear characteristics of the coupled inductor, the static and dynamic natural characteristics of the inverter are optimized. The modular power superposition of the inverter is achieved through phase-shifting superposition.

[0070] When the inverter topology is a single-module coupled structure, the interleaved high-frequency power switch is the interleaved high-frequency power switch within a single module, and the power coupling element is the power coupling element within a single module; such as Figure 1 As shown, the interleaved high-frequency power switch T 11 ~T 14 Together with complementary low-frequency power switches T5-T6, they form an inverter bridge, with switch T... 11 ~T 14 This is a high-frequency switch with bidirectional current flow and a 180-degree phase difference, where switching transistors T5 and T6 are low-frequency switches with a modulation wave frequency. 11 T 13 The drain of T5 and the input voltage V dc The positive terminals are connected, T 12 T 14 The source of T6 and the input voltage V dc The negative terminals are connected, T 11 The source and T 12 The drain terminals are connected to form the midpoint a of the bridge arm; T 13 The source and T 14 The drains of T5 and T6 are connected to form the midpoint b of the bridge arm; the source of T5 and the drain of T6 are connected to form the midpoint c of the bridge arm; point a is connected to the inductor L. 11 One end is connected, and point b is connected to inductor L. 12 One end is connected, L 11 With L 12 The other end is connected in parallel to form node d, L 11 L 12 Reverse coupling; node d is connected to one end of the output filter capacitor C0 to form the inverter output terminal "+", and the other end of C0 is connected to point c to form the other output terminal "-", and the output load R L Connect in parallel with the positive and negative terminals of the output;

[0071] In a single-module coupled inverter topology, the interleaved high-frequency power switch T 11 T 12 With T 13 T 14 They are 180° apart in timing, meaning they work in staggered phases, 180° apart.

[0072] When the inverter topology is a multi-module coupled structure, the interleaved high-frequency power switch is the interleaved high-frequency power switch within the multi-module, and the power coupling element is the power coupling element within the multi-module; the interleaved high-frequency power switch T 11 ~T 14 T i1 ~T i4 (i = 2, 3, ..., n) and the complementary low-frequency power switches T5 to T6 form multiple inverter bridges, with multiple modules interleaved with high-frequency power switches T i1 T i2 With T i3 T i4 A 180° phase shift, i.e., interleaved operation, reduces the phase shift angle between the inverter bridges of adjacent modules. n represents the total number of high-frequency switching modules, i.e., phase-shifted superposition.

[0073] Modular power superposition of inverters is achieved through phase-shift superposition. Specifically, to increase power, a high-frequency switching module T is added. i1 ~T i4 (i = 2, 3, ..., n); Increase the phase shift between adjacent modules, that is, the phase shift angle between inverter bridges. n represents the total number of high-frequency switching modules. This is achieved by stacking inverter modules through phase shifting and using interleaved control to expand power output. See the detailed circuit connection diagram below. Figure 2 .

[0074] The coupling inductors of a single module adopt a reverse coupling method, and their coupling coefficient K = 0.1 to 0.9.

[0075] like Figure 3 As shown, the coupling methods of the coupled inductor include loose coupling, loose-tight coupling, and distributed coupling structures.

[0076] Both the interleaved high-frequency power switch and the complementary low-frequency power switch are SiCMOS transistors.

[0077] The filtering element is an output filtering inductor, and its design formula is as follows:

[0078]

[0079] In the formula: L f —Filter inductor (H); V0 —Output voltage (V); f s —Switching frequency (Hz); D kmin —Minimum duty cycle at the highest voltage; ΔI —Inductor current ripple, ΔI=0.4I0;

[0080] The formula for calculating the core area of ​​an inverter is:

[0081]

[0082] In the formula: A P — Area of ​​the magnetic core (cm²) 2 );I pk — Peak current (A); B — Magnetic flux density (T); J — Current carrying capacity of conductor (A / cm³) 2 ); K n —Window utilization rate, ranging from 0.3 to 0.5; where L f The larger the core area, the larger the inverter core area, which means the heavier the inverter.

[0083] The inverter topology reduces the inverter's weight by decreasing the output filter inductance. Specifically, it employs an integrated coupled inductor topology based on interleaved superposition, utilizing the nonlinear characteristics of the coupled inductors to increase the static inductance and reduce the dynamic inductance, thereby enhancing the inverter's static and dynamic natural characteristics. The coupled inductors are two-way, and their static inductance is calculated using the following formula:

[0084]

[0085]

[0086] The sum of the static inductances during one switching cycle is:

[0087]

[0088] The dynamic inductance is:

[0089] L 动 = (1-K)L Formula Six;

[0090] Formulas three, four, five, and six,

[0091] D k —Duty cycle of the Kth pulse; D′ k ——1-D k L—Self-inductance, L i (i = 1, 2) — Self-inductance of the two inductors; K — Coupling coefficient (L1 = L2 = L); M — mutual inductance;

[0092] From formulas three, four, and five, it can be seen that the static inductance after coupling is greater than that of the discrete inductor, and the inductance is related to the duty cycle. When D = 0.5, the static inductance is minimized, and the calculation formula is as follows:

[0093] L 静min =2(1+K)L(K>0) Formula 7.

[0094] The inverter is a single-phase inverter with a wide input voltage range;

[0095] like Figure 4 As shown, its modulated wave u(t) = U m During the positive half-cycle of sinω0t; T6 is normally on, T5 is off; one switching cycle T consists of two sawtooth wave cycles. S (f s The period of the carrier sawtooth wave During the positive half-week, T 12 T 14 Turn off, T 11 T 13 With T L It operates with alternating switching cycles;

[0096] During the period from t0 to t1, T 11 T6 is on, T 12 T 13 T 14 T5 off, V dc Through T 11 L 11 C0 and T6 form a loop, V dc Power is supplied to the load; at the same time, T 14 junction diodes VD4 and L 12 C0 and T6 form a freewheeling loop for the i2(+) current.

[0097] During the period t1 to t2, T 11 T 12 T 13 T 14 When T5 is off and T6 is on, the i2(+) freewheeling circuit operates in the same manner as t0 to t1. 12 junction diodes VD2 and L 11 C0 and T6 form a freewheeling loop for the i1(+) current.

[0098] During the period from t2 to t3, T 13 T6 is on, T 11 T 12 T 14 T5 off, V dc Through T 13 L 12 C0 and T6 form a loop, V dc Power is supplied to the load; the i2(+) freewheeling circuit is the same as the t1~t2 process.

[0099] The working process from t3 to t4 is the same as the working process from t1 to t2;

[0100] During the operating periods t0~t1 and t2~t3, the coupling inductance L 11 L 12As a static inductor, according to formulas three, four, and five, its static inductance L is... 静 Larger than discrete inductors (L 11 +L 12 );

[0101] During the operating periods t1~t2 and t3~t4, the coupling inductance L 11 L 12 As a dynamic inductor, according to Formula 6, its dynamic inductance L 动 Smaller than discrete inductor L 11 L 12 .

[0102] Example:

[0103] In this example, to verify the invention, the circuit was simulated. The simulation used a single-module coupled inverter topology as shown below. Figure 5 As shown, the inverter uses unipolar modulation, and T5 and T6 are low-frequency transistors that are switched on and off at the power frequency. 11 T 12 T 13 T 14 It is a high-frequency transistor. During the positive half-cycle of the output voltage, T 11 T 13 Alternating high-frequency on / off states. During the negative half-cycle of the output voltage, T... 12 T 14 Alternating high-frequency switching. To enable high-frequency switching and achieve soft switching, the current flowing through L... 11 L 12 The currents i1 and i2 are in discontinuous / critical state.

[0104] The circuit parameters of the simulation model are shown in Table 1.

[0105] Table 1 Circuit component parameters

[0106]

[0107]

[0108] Figure 6 This is the theoretical waveform of the inverter inductor current. Taking the positive half-cycle of the output voltage as an example, we analyze the circuit's operating state.

[0109] Figure 7 The figures show the simulated waveforms of inductor current and bridge arm voltage. A simulation model was built in MATLAB / Simulink, with the output voltage reference value set to an effective value of 220V and a frequency of 50Hz. The changing patterns of the inductor current and voltage verify the results of the above analysis.

[0110] Figure 8This is a simulation waveform of the bridge arm voltages after filtering. In the Simulink simulation, the waveforms of the bridge arm output voltages uan1 and uan2 are passed through a low-pass filter with a cutoff frequency of 10kHz, and the output waveforms are as follows. Figure 8 As shown.

[0111] Figure 9 These are the waveforms of the inverter's output voltage and current. Through simulation verification, the desired modulation wave meets the requirements.

[0112] Mode The independent inductance L when uncoupled 独 According to the present invention, the static inductance is calculated as follows:

[0113]

[0114] The simulation shows that:

[0115] 1) It can definitely achieve soft switching of power switching devices and reduce power switching losses.

[0116] 2) The filter parameters were reduced, resulting in the filter's cutoff frequency:

[0117]

[0118] This increases the overall power density of the system (compared to the conventionally designed filter cutoff frequency f). c (≈1000~2000Hz).

Claims

1. A phase-shifted interleaved power stacked + magnetic integrated inverter topology, characterized by: The inverter topology comprises interleaved high-frequency power switching tubes, power coupling elements, complementary low-frequency power switching tubes and filter elements; the power coupling elements comprise coupling inductors with nonlinear characteristics; The interleaved high-frequency power switching tubes, the complementary low-frequency power switching tubes and the integrated power coupling elements form a single-module or multi-module coupled inverter topology; the switching tubes in the single-module coupled inverter topology are in interleaved working conditions, and the inverter bridges in the multi-module coupled inverter topology are in phase-shifted and superimposed working conditions; the nonlinear characteristics of the coupling inductors are used to increase static inductance and reduce dynamic inductance, so as to optimize the static and dynamic natural characteristics of the inverter; the modularity of the inverter is realized by phase-shifted superposition and power superposition. When the inverter topology is a single module coupling structure, the interleaved high-frequency power switch is a single module interleaved high-frequency power switch, and the power coupling element is a single module power coupling element; the interleaved high-frequency power switch T 11 ~T 14 and the complementary low-frequency power switch T5~T6 form an inverter bridge, the interleaved high-frequency power switch T 11 ~T 14 is a 180-degree interleaved high-frequency switch with bidirectional current flow, the complementary low-frequency power switch T5, T6 is a low-frequency switch with modulation wave frequency, the drain of T 11 , T 13 , T5 is connected to the positive pole of the input voltage V dc , the source of T 12 , T 14 , T6 is connected to the negative pole of the input voltage V dc , the source of T 11 is connected to the drain of T 12 to form a bridge arm midpoint a; the source of T 13 is connected to the drain of T 14 to form a bridge arm midpoint b; the source of T5 is connected to the drain of T6 to form a bridge arm midpoint c; the a point is connected to one end of the inductor L 11 , the b point is connected to one end of the inductor L 12 , L 11 and L 12 are connected in parallel to form a node d, L 11 , L 12 are reversely coupled; the node d is connected to one end of the output filter capacitor C0 to form an inverter output "+", the other end of C0 is connected to the c point to form another output "-", and the output load R L is connected in parallel with the positive and negative poles of the output. In the single module coupled inverter topology, the interleaved high-frequency power switch tubes T 11 , T 12 and T 13 , T 14 are 180° staggered in time, that is, staggered by 180 degrees.

2. The phase-shifted interleaved power stacked + magnetic integrated inverter topology of claim 1, wherein: When the inverter topology is a multi-module coupling structure, the interleaved high-frequency power switch tube is an interleaved high-frequency power switch tube within a multi-module, and the power coupling element is a power coupling element within the multi-module; the interleaved high-frequency power switch tube T 11 ~T 14 , T i1 ~T i4 (i=2, 3, ···, n) and the complementary low-frequency power switch tubes T5~T6 form a plurality of inverter bridges, and the interleaved high-frequency power switch tubes T i1 , T i2 and T i3 , T i4 are 180° out of phase, that is, interleaved operation, so that the phase shift angle between the inverter bridges of adjacent modules and the inverter bridges is n is the total number of high-frequency switch modules, that is, phase shift superposition.

3. The phase-shifted interleaved power stacked + magnetic integrated inverter topology of claim 2, wherein: The modular power superposition of the inverter is realized by phase shift superposition, and the method is as follows: when the power is expanded, the staggered high-frequency power switch tube T i1 ~T i4 (i=2, 3, ···, n) of the i-th module is increased; the phase shift between adjacent modules, i.e. the phase shift angle between the inverter bridges, is increased n is the total number of high-frequency switch modules, i.e. the inverter modules are superimposed by phase shift, and the power is expanded by staggered control.

4. The phase-shifted interleaved power stacked + magnetic integrated inverter topology of claim 2, wherein: The coupling inductors of a single module adopt a reverse coupling mode, and the coupling coefficient K is 0.1-0.

9.

5. The phase-shifted interleaved power stacked + magnetic integrated inverter topology of claim 1, wherein: The coupling mode of the coupling inductors comprises loose coupling, loose-tight coupling and distributed coupling.

6. The phase-shifted interleaved power stacked + magnetic integrated inverter topology of claim 1, wherein: The interleaved high-frequency power switching tubes and the complementary low-frequency power switching tubes are SiC MOS tubes.

7. The phase-shifted interleaved power stacked + magnetic integrated inverter topology of claim 1, wherein: The filter element is an output filter inductor, and the design formula is where: L f — filter inductance (H); V0— output voltage (V); f s — switching frequency (Hz); D kmin — minimum duty cycle at maximum voltage; ΔI— inductance current ripple, ΔI = 0.4I0; The magnetic core area calculation formula of the inverter is In the formula: A P Area of the magnetic core (cm 2 ); I pk Peak current (A); B - magnetic induction (T); J - current carrying capacity of the wire (A / cm 2 ); K n Window utilization, the value range is 0.3-0.5; In the formula L f The greater the window utilization is, the greater the area of the magnetic core of the inverter is, that is, the heavier the inverter is.

8. The phase-shifted interleaved power stacked + magnetic integrated inverter topology of claim 7, wherein: The inverter topology makes the inverter lightweight by reducing the output filter inductor, that is, on the basis of interleaved superposition, the integrated coupling inductor topology is adopted, the nonlinear characteristics of the coupling inductor are used to increase static inductance, reduce dynamic inductance and enhance the static and dynamic natural characteristics of the inverter; the coupling inductor is two-way, and the calculation formula of the static inductance is In one switching cycle, the sum of the static inductance is: The dynamic inductance is: L 动 = (1 - K)L Equation Six; In formulas three, four, five and six, D k — duty cycle of the Kth pulse; D' k — 1-D k ; L — self-inductance, L i (i = 1, 2) — self-inductance of the two inductances; K — coupling factor (L1= L2= L); M — mutual inductance; From Formulas III, IV, and V, it can be seen that the static inductance after coupling is greater than that of the separated inductor, and the inductance is related to the duty cycle. When D = 0.5, the static inductance is minimum, and the calculation formula is L 静min = 2(1 + K)L(K > 0) Formula VII.

9. The phase-shifted interleaved power stacked + magnetic integrated inverter topology of claim 8, wherein: The inverter is a single-phase inverter with a wide input voltage range. Its modulation wave u(t) = U m sin ω0t positive half cycle; T6 always on, T5 off; with two sawtooth wave periods as a switching period T S (f S ), the period of the carrier sawtooth wave (f L = 2f S ), in the positive half cycle, T 12 , T 14 off, T 11 , T 13 with T L as the switching period staggered operation; T 11 , T 12 , T 13 , T 14 , T dc , T 11 , L 11 , C0, T dc , T 14 , T 12 , T t1~t2, T 11 , T 12 , T 13 , T 14 , T5 off, T6 on, i2(+) freewheeling loop same as t0~t1 process; T 12 diode VD2, L 11 , C0, T6 form i1(+) current freewheeling loop; During the period from t2 to t3, T 13 T6 is on, T 11 T 12 T 14 T5 off, V dc Through T 13 L 12 C0 and T6 form a loop, V dc Power is supplied to the load; the i2(+) freewheeling circuit is the same as the t1~t2 process; the working process of t3~t4 is the same as the working process of t1~t2. During the operation period of t0~t1 and t2~t3, the coupling inductance L 11 , L 12 is the static inductance, according to the formulas three, four and five, the static inductance L 静 is greater than the separated inductance L' 11 +L' 12 ; t1~t2 and t3~t4 working period, coupling inductance L 11 , 12 Dynamic inductance, according to formula six, its dynamic inductance L 动 Less than the split inductance L' 11 , 12 .

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