A monopole array combined with a transmissive array microwave millimeter wave three-frequency co-aperture antenna

Abstract

The application provides a microwave millimeter wave three-frequency co-aperture antenna combining a monopole array and a transmission array, comprising a plurality of layers of PCB boards, the plurality of layers of PCB boards comprising a first dielectric plate, a second dielectric plate, a third dielectric plate, a fourth dielectric plate, a fifth dielectric plate and a sixth dielectric plate, the surfaces of the first dielectric plate, the second dielectric plate, the third dielectric plate, the fourth dielectric plate, the fifth dielectric plate and the sixth dielectric plate are provided with metal layers, the metal layers on the first dielectric plate, the second dielectric plate, the third dielectric plate and the fourth dielectric plate are provided with rectangular patches, the peripheries of the rectangular patches are provided with annular slots, the annular slots are connected with the rectangular slots, the metal layers are further provided with a first slot and a second slot, and the metal layer of the fourth dielectric plate is further provided with a microwave frequency band feed network; the metal layer of the fifth dielectric plate is provided with an I-shaped slot; and the metal layer of the sixth dielectric plate is provided with a microstrip antenna. The application can effectively realize high aperture utilization, high structural multiplexing rate and miniaturization of the overall antenna.

Description

TECHNICAL FIELD

[0001] The present application relates to the technical field of antennas, in particular to a microwave and millimeter wave three-frequency co-aperture antenna combining monopole array and transmission array. BACKGROUND

[0002] In recent years, the microwave / millimeter wave coexistence problem has attracted extensive attention from the academic and industrial circles. This is mainly because the microwave and millimeter wave frequency bands are different in specific communication methods and uses. The microwave frequency band is often used for long-distance non-line-of-sight communication, while the millimeter wave frequency band is often used for short-distance high-speed line-of-sight communication. With the continuous development of communication technology, communication systems are developing towards multi-standard, multi-standard and multi-function. Therefore, in future communication systems, microwave and millimeter wave frequency bands will exist in the same system, and they will complement each other in function, ultimately achieving high-quality and close communication between devices. As an important component of the communication system, the antenna system therefore needs to have the ability of microwave / millimeter wave coexistence.

[0003] At present, co-aperture antennas are an efficient antenna solution for microwave / millimeter wave coexistence. This solution combines two or more different types of antennas through partial or complete structural reuse, thereby achieving the purpose of microwave / millimeter wave coexistence. In documents [1]-[4], the design of co-aperture antennas with structural reuse of Fabry-Perot cavity / parallel plate waveguide resonator, patch antenna / slot antenna, dipole / dipole array, patch antenna / substrate integrated waveguide array is proposed respectively.

[0004] Currently, although there are many designs of co-boresight antennas reported in the open literature, there are still some problems worth solving, which include: 1) Most of the co-boresight antennas reported only work in dual-band, i.e. one microwave band and one millimeter-wave band. However, for the 5G communication system, there are already many millimeter-wave bands divided, such as 26 GHz, 39 GHz, 43 GHz, 52 GHz, 77 GHz, etc. If the dual-band or multi-band of millimeter-wave bands can be further realized on the basis of the coexistence of microwave and millimeter-wave, the functionality and flexibility of the system can be greatly improved, but currently there is relatively little research on this aspect; 2) The co-boresight antennas reported in the design pay more attention to the high gain characteristics of the millimeter-wave band, and the gain characteristics of the microwave band are rarely discussed. This is mainly because the electromagnetic wave in the millimeter-wave band has a high propagation loss in the atmosphere, so high gain is usually needed to compensate. But in fact, the microwave band also needs high gain when communicating over long distances. There are relatively few designs that can achieve high gain in microwave and millimeter-wave dual-band at the same time; 3) In order to achieve high gain in the millimeter-wave band, the antenna in this band often needs to form an antenna array. However, the traditional antenna array usually needs a large and complex feed network, which will also cause the antenna to have high feed loss, complexity, and high design difficulty in the millimeter-wave band. At the same time, the existence of the feed network will greatly limit the design of the co-boresight antenna.

[0005] [1] L. Y. Feng and K. W. Leung, “Dual-Frequency Folded-Parallel-PlateAntenna With Large Frequency Ratio,” IEEE Trans. Antennas Propag. , vol. 64,no. 1, pp. 340-345, Jan. 2016.

[0006] [2] Y. -X. Sun and K. W. Leung, “Substrate-Integrated Two-Port Dual-Frequency Antenna,” IEEE Trans. Antennas Propag. , vol. 64, no. 8, pp. 3692-3697, Aug. 2016.

[0007] [3] J. Lan, Z. Yu, J. Zhou and W. Hong, “An Aperture-Sharing Array for (3.5, 28) GHz Terminals With Steerable Beam in Millimeter-Wave Band,” IEEE Trans. Antennas Propag. , vol. 68, no. 5, pp. 4114-4119, May 2020.

[0008] [4] J. F. Zhang, Y. J. Cheng, Y. R. Ding and C. X. Bai, “A Dual-Band Shared-Aperture Antenna With Large Frequency Ratio, High Aperture Reuse Efficiency, and High Channel Isolation,” IEEE Trans. Antennas Propag. , vol.67, no. 2, pp. 853-860, Feb. 2019. SUMMARY

[0009] In order to at least solve one of the problems existing in the prior art, the present application provides a microwave millimeter wave three-frequency co-aperture antenna combining a monopole array and a transmissive array structure. Through structural multiplexing, the monopole array and the transmissive array are integrated in the same aperture plane, which can effectively realize high aperture utilization, high structural multiplexing rate and miniaturization of the overall antenna. Since the transmissive array antenna itself adopts a spatial feeding feeding mode, the antenna does not need a complex feeding network in the millimeter wave frequency band, and has the advantages of low feeding loss, high gain, etc. At the same time, since the present application also adopts an array form in the microwave frequency band, high gain characteristics can be realized in both frequency bands at the same time.

[0010] In order to achieve the purpose of the present application, the present application provides a microwave millimeter wave three-frequency co-aperture antenna combining a monopole array and a transmissive array, which comprises a plurality of layers of PCB boards,

[0011] The multilayer PCB comprises a first dielectric plate, a second dielectric plate, a third dielectric plate, a fourth dielectric plate, a fifth dielectric plate and a sixth dielectric plate, and the surfaces of the first dielectric plate, the second dielectric plate, the third dielectric plate, the fourth dielectric plate, the fifth dielectric plate and the sixth dielectric plate are provided with metal layers, wherein the metal layers on the first dielectric plate, the second dielectric plate, the third dielectric plate and the fourth dielectric plate are provided with rectangular patches, the periphery of each rectangular patch is provided with an annular gap, and the annular gap is connected with a rectangular gap, the metal layer is further provided with a first gap arranged periodically and a second gap arranged on both sides of the first gap, and the metal layer of the fourth dielectric plate is further provided with a microwave frequency band feed network; the metal layer of the fifth dielectric plate is provided with periodically arranged I-shaped gaps; and the metal layer of the sixth dielectric plate is provided with two microstrip antennas working at different millimeter wave frequency bands.

[0012] Further, the two microstrip antennas work at 26GHz and 39GHz frequency bands respectively.

[0013] Further, a distance is left between the two microstrip antennas.

[0014] Further, the microwave frequency band and the two millimeter wave frequency bands are respectively fed by three coaxial connectors with a characteristic impedance of 50 ohms.

[0015] Further, the support structure is further provided, and the first dielectric plate, the second dielectric plate, the third dielectric plate, the fourth dielectric plate and the fifth dielectric plate are fixed on the support structure.

[0016] Further, the dielectric support is further provided, and the dielectric support is located below the support structure, the dielectric support comprises an upper dielectric plate and a lower dielectric plate arranged oppositely, and the fifth dielectric plate and the sixth dielectric plate are respectively located on the upper dielectric plate and the lower dielectric plate.

[0017] Further, the beam scanning of the millimeter wave frequency band is realized by changing the position of the sixth dielectric plate on the lower dielectric plate.

[0018] Further, the microwave frequency band feed network comprises a first-stage microstrip line power divider, a second-stage microstrip line power divider, a transition structure and a coplanar waveguide, the first-stage microstrip line power divider is an equal-amplitude differential power divider, and two output signals have the same output amplitude, the second-stage microstrip line power divider outputs signals with the same amplitude and the same phase, and the transition structure is used for realizing the conversion between the second-stage microstrip line power divider and the coplanar waveguide.

[0019] Further, the transition structure is a microstrip line with gradually changing width.

[0020] Further, the rectangular patches on the first dielectric plate, the second dielectric plate, the third dielectric plate and the fourth dielectric plate are provided with four rectangular patches arranged in a 2x2 array, each rectangular patch is provided with an annular gap, and each annular gap is connected with a rectangular gap.

[0021] Compared with the prior art, the present application can at least achieve the following beneficial effects:

[0022] (1) Most of the microwave / millimeter wave co-caliber antennas reported at present are dual-band, and the present application proposes a tri-band co-caliber antenna.

[0023] (2) The co-caliber antenna in the present application adopts the mode of patch and transmission array multiplexing, and due to the spatial feeding characteristics of the transmission array antenna, the present application has the advantages of no need for complex feeding network, low feeding loss, high gain, etc. in the millimeter wave frequency band.

[0024] (3) In the present application, the patch and the transmission array are in a completely multiplexed relationship in structure, and therefore the present application has the advantage of high aperture multiplexing rate.

[0025] (4) The antenna in the present application works in the 3.5 GHz microwave frequency band and the 26 GHz and 39 GHz millimeter wave frequency bands. In the microwave and millimeter wave frequency bands, the antenna works in the form of 2x2 monopole array and transmission array, respectively. BRIEF DESCRIPTION OF DRAWINGS

[0026] Fig. 1 is a three-dimensional structure schematic diagram of a microwave millimeter wave tri-band co-caliber antenna with monopole array and transmission array structure multiplexing provided by an embodiment of the present application.

[0027] Fig. 2 is a top view of a first dielectric plate and a first metal layer on the surface thereof in an embodiment of the present application.

[0028] Fig. 3 is a top view of a fourth dielectric plate and a second metal layer on the surface thereof in an embodiment of the present application.

[0029] Fig. 4 is a top view of a fifth dielectric plate and a third metal layer on the surface thereof in an embodiment of the present application.

[0030] Fig. 5 is a top view of a sixth dielectric plate and a fourth metal layer on the surface thereof in an embodiment of the present application.

[0031] Fig. 6 is a schematic diagram of the design evolution process of the antenna in an embodiment of the present application.

[0032] Fig. 7 is a structure schematic diagram of a transmission array element in an embodiment of the present application.

[0033] Fig. 8 is a schematic diagram of the relationship between the transmission coefficient and the transmission phase of the transmission array element working at 26 GHz and 39 GHz and the parameters L1 (a figure) and L2 (b figure) of the "one" type slot.

[0034] Fig. 9 Schematic diagram of the performance of the "I"-shaped gap in an embodiment of the present invention.

[0035] Fig. 10 Schematic diagram of the S-parameter performance of the antenna in an embodiment of the present invention.

[0036] Fig. 11 This is the directional pattern of the antenna in the embodiment of the present invention operating at 3.5 GHz.

[0037] Fig. 12 This is the directional pattern of the antenna in the embodiment of the present invention operating at 26 GHz.

[0038] Fig. 13 : is the directional pattern of the antenna in the embodiment of the present invention operating at 39 GHz.

[0039] Fig. 14 Schematic diagram of antenna gain in three frequency bands in an embodiment of the present invention.

[0040] Fig. 15 : is the beam scanning pattern of the antenna in the embodiment of the present invention operating at 26 GHz.

[0041] Fig. 16 This is the beam scanning pattern of the antenna in the embodiment of the present invention operating at 39 GHz. DETAILED DESCRIPTION

[0042] To make the objectives, technical solutions, and advantages of the embodiments of the present invention more clear, the technical solutions in the embodiments of the present invention will be clearly and completely described below in conjunction with the accompanying drawings of the embodiments of the present invention. Obviously, the described embodiments are only part of the embodiments of the present invention, not all of the embodiments. Based on the embodiments of the present invention, all other embodiments obtained by ordinary technicians in this field without making creative efforts are within the scope of protection of the present invention.

[0043] The present invention provides a microwave and millimeter wave triple-frequency co-aperture antenna that multiplexes a monopole array and a transmission array structure. The full view is as follows: Fig. 1 As shown. The following coordinate system is established: the x-axis and y-axis of the rectangular coordinate system are parallel to the two edges of the PCB board, and the antenna's maximum radiation direction points in the positive direction of the z-axis. The entire antenna consists of three parts: a multilayer PCB board, a support structure 17, and a dielectric bracket 18.

[0044] The PCB board has a total of six layers, including a first dielectric board 11, a second dielectric board 12, a third dielectric board 13, a fourth dielectric board 14, a fifth dielectric board 15, and a sixth dielectric board 16, which are arranged in sequence. In some embodiments of the present invention, the PCB board material used is Rogers 5880, with a dielectric constant of 2.2 and a dielectric loss tangent of 0.0009. The thicknesses of the first dielectric board 11 to the sixth dielectric board 16 are 0.254 mm, 0.254 mm, 0.254 mm, 0.254 mm, 0.254 mm, and 0.508 mm, respectively. The board spacings are 2.5 mm, 2.5 mm, 2.5 mm, 20 mm, and 25.5 mm, respectively. The size of each PCB board is 130 mm × 130 mm. The feeding of the three frequency bands all uses a 50-ohm coaxial connector, and the feeding ports are port 1 (3.5 GHz), port 2 (26 GHz) and port 3 (39 GHz). Port 1 is located on the fourth dielectric plate 14, and port 2 and port 3 are located on the sixth dielectric plate 16.

[0045] The top view of the first dielectric plate 11 and the first metal layer 21 on its surface is shown in FIG. Fig. 2 As shown. Four rectangular patches 22 of the same size are provided on the first metal layer 21, and an annular gap 23 is provided around each rectangular patch 22. The four rectangular patches 22 form a 2×2 array, and the array element spacing along the x-axis and y-axis directions is 0.56λ0 (λ0 is the free space wavelength corresponding to 3.5GHz). Four rectangular gaps 24 are also provided on the first metal layer 21, and each rectangular gap 24 is connected to the corresponding annular gap 23. Two types of "I"-shaped first gaps 25 and second gaps 26 are also provided within the area of ​​the first metal layer 21. Both gaps are arranged periodically, and the second gaps 26 are symmetrically arranged on both sides of the first gap 25. The two gaps are arranged alternately. In some embodiments of the present invention, the period size is 5.5 mm.

[0046] The second dielectric plate 12 and the third dielectric plate 13 are completely identical in structure to the first dielectric plate 11 , and the metal layers and the first metal layer 21 on the surfaces of the second dielectric plate 12 and the third dielectric plate 13 are also identical.

[0047] The top view of the fourth dielectric plate 14 and the second metal layer 31 provided on the surface thereof is shown in FIG. Fig. 3As shown. A microwave frequency band feeding network is provided on the second metal layer 31, and the microwave frequency band feeding network includes a first-stage microstrip line power divider 32, a second-stage microstrip line power divider 33, a transition structure 34 and a coplanar waveguide 35. The first-stage microstrip line power divider 32 is an equal-amplitude differential power divider, that is, the two output signals have the same output amplitude and a phase difference of 180 degrees. The signals output by the second-stage microstrip line power divider 33 are equal in amplitude and in phase. The transition structure 34 is a microstrip line with a gradient width, which is used to realize the conversion between the second-stage microstrip line power divider 33 and the coplanar waveguide. Similar to the first metal layer 21, the second metal layer 31 is also provided with a rectangular patch 22, an annular gap 23 and two "I"-shaped gaps - a first gap 25 and a second gap 26.

[0048] The top view of the fifth dielectric plate 15 and the third metal layer 41 disposed on the surface thereof is shown in FIG. Fig. 4 The third metal layer 41 is provided with periodically arranged "I"-shaped gaps 42. This dielectric plate is a frequency selective surface. In some embodiments of the present invention, the period is 5.6 mm.

[0049] Support structure 17 secures the first dielectric plate 11 to the fifth dielectric plate 15 while ensuring proper spacing between the plates. A dielectric bracket 18 secures the fifth dielectric plate 15 and the sixth dielectric plate 16. Located below support structure 17, bracket 18 comprises two opposing upper and lower dielectric plates, connected by dielectric columns. The fifth dielectric plate 15 and the sixth dielectric plate 16 are located on the upper and lower dielectric plates, respectively. Beam scanning in the millimeter-wave band is achieved by moving the sixth dielectric plate 16 in the x-direction from its fixed position on bracket 18.

[0050] The sixth dielectric plate 16 and the fourth metal layer 51 provided on the surface thereof are as follows: Fig. 5 As shown, two rectangular microstrip antennas are provided on the fourth metal layer 51, namely a first microstrip antenna 52 and a second microstrip antenna 53. There is a distance between the first microstrip antenna 52 and the second microstrip antenna 53. In some embodiments of the present invention, the distance between the first microstrip antenna 52 and the second microstrip antenna 53 is 20 mm.

[0051] In terms of working principle, the design evolution of antenna structure is as follows Fig. 6 As shown, we first start from the basic antenna prototype of antenna one, then go through the structural evolution of antenna two and antenna three, and finally get the antenna design (antenna four) provided by the present invention. Each antenna structure is in Fig. 6The antenna is illustrated by side view and top view. Antenna one is a traditional monopole antenna fed by a coplanar waveguide. In order to obtain higher gain and symmetrical pattern, the monopoles are arranged into a 2x2 array based on antenna one, and then the design of antenna two is proposed. In this design, the array is mirror symmetrical along the y direction, so the differential feed is used to form the high-gain edge-on pattern. The feed network of the array is a two-stage 1-to-2 microstrip power divider, which is excited by port 1. The first-stage microstrip power divider uses unequal-length transmission lines to achieve differential output, and microstrip-to-coplanar waveguide transitions are provided at the four output ports. In order to be combined with the transmitarray antenna, the monopole array is stacked with three layers of the same structure at equal intervals along the z-axis direction. Since the board spacing of this multi-layer structure is very small, about 0.03λ0, the performance of the antenna in the microwave frequency band will not be severely affected after introducing the multi-layer PCB board. At this time, the antenna structure can be regarded as an array structure with thick metal layers. Subsequently, the peripheral rectangular patch 22 is added to antenna two, which is separated from the monopole array elements by a ring-shaped gap 23, and two "I" type slots are introduced on each layer of the PCB board, thereby forming the structure of antenna three. After introducing the peripheral rectangular patch 22, the operating frequency of the monopole array will be slightly shifted, and this frequency shift can be optimized by changing the width of the ring-shaped gap 23. The two "I" type slots constitute the array element of the transmitarray. Since the sizes of the two slots are much smaller than λ0, these slots can be regarded as extremely small structures in the microwave frequency band, and they will not have a great impact on the operating performance in the microwave frequency band. In order to obtain a suitable focal ratio of the transmitarray antenna, the metal ground plate is replaced by a frequency selective surface arranged with multiple "H" type slots on the basis of antenna three, and two feed sources 1 and 2 operating at 26 GHz and 39 GHz are added. The frequency selective surface has a passband in the millimeter wave frequency band and a stopband in the microwave frequency band, so it can make the electromagnetic waves in the millimeter wave frequency band pass through unobstructed, while reflecting the electromagnetic waves in the microwave frequency band. The feed sources 1 and 2 are both microstrip patch antennas, excited from port 2 and port 3 respectively. The working principles of the two feed source antennas are the same, but they work at different frequencies due to their different sizes. In the millimeter wave frequency band, electromagnetic waves are emitted from the lower feed source, then pass through the frequency selective surface to illuminate the transmitarray array surface composed of multiple layers of PCB boards, and the incident spherical wave is converted into a plane wave through the phase modulation of the array surface, and finally radiated into the atmosphere. In the microwave frequency band, the frequency selective surface acts as a metal ground plate (reflection plate) of the monopole array, which has the same effect as the traditional metal ground plate.

[0052] The structure of the transmitarray array element is shown in Fig. 7As shown. The middle "I" shaped gap can be divided into two equal gaps, each with a length of L1 / 2, and a total length of L1. Two "I" shaped gaps with a length of L2 are symmetrically distributed on both sides. The change of transmission phase is achieved by adjusting the values ​​of parameters L1 and L2, as shown Fig. 8 As shown, for a unit operating at 26 GHz, by adjusting the phase by varying the parameter L1, when L1 changes from 4.3 mm to 5.4 mm, the transmission phase achieves 360° phase coverage, and the transmission phase fluctuation in the 39 GHz band is minimal. Similarly, for a unit operating at 39 GHz, by adjusting the phase by varying the parameter L2, when L2 changes from 3.0 mm to 3.7 mm, the transmission phase achieves 360° phase coverage, and the transmission phase in the 26 GHz band remains virtually unchanged. This demonstrates that the transmission phase coupling between the units in the two frequency bands is very low, enabling independent phase shifting in both bands. Furthermore, the transmission loss of the units in both frequency bands is very low, indicating that electromagnetic waves can effectively pass through the array. By utilizing the principle of equal path difference, multiple units can be arranged to form a transmission array. Considering the illumination efficiency and spillover efficiency of the transmission array, in some embodiments of the present invention, a focal ratio parameter of 0.65 is selected.

[0053] The performance of the I-shaped slot unit in the frequency selective surface is as follows Fig. 9 As shown in the figure, the reflection coefficient amplitude of this unit in the microwave band is close to 1, and the reflection phase is close to 180°, indicating that this frequency-selective surface exhibits total reflection characteristics in the microwave band, which is the same as the performance of traditional metal floors. Therefore, it can be used as a reflector for monopole arrays in the microwave band. In the millimeter wave band, the transmission coefficient of this unit is close to 1, and the reflection coefficient is less than 0.3 (approximately -10dB), indicating that electromagnetic waves in the millimeter wave band (26GHz and 39GHz) can pass through this frequency-selective surface well. When emitted by the feed source, electromagnetic waves in the millimeter wave band can pass directly through this surface to the transmission array face.

[0054] In terms of antenna performance, S parameters such as Fig. 10 As shown in the figure, it can be seen that in the ranges of 3.41-3.57GHz, 25.2-26.7GHz and 37.0-40.4GHz, the antenna can achieve -10dB impedance matching. At the same time, the isolation between port 2 and port 3 is higher than 30dB, which means that the antenna can operate at 3.5GHz, 26GHz and 39GHz, and the port isolation is good. The directional patterns at 3.5GHz, 26GHz and 39GHz are shown in Figure 1. Fig. 11 、 Fig. 12 and Fig. 13 As shown, it can be seen that the antenna has the characteristics of low sidelobe and low cross-polarization in all three frequency bands, and the radiation pattern performance is good. Fig. 14The antenna gain in three frequency bands is shown, and it can be seen that the peak gain in three frequency bands is 12.3dBi, 18.7dBi and 22dBi respectively. In combination with the radiation pattern results, it can be seen that the antenna has good radiation performance, high gain, and stable gain in each frequency band. Fig. 15 and Fig. 16 The beam scanning radiation patterns at 26GHz and 39GHz are shown respectively. Under the condition of 3-dB gain roll-off, the antenna can achieve a scanning angle range of ±27° and ±24° in two millimeter wave frequency bands respectively, and has good scanning performance.

[0055] The above description of disclosed embodiments enables one skilled in the art to make or use the application. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein can be applied to other embodiments without departing from the spirit or scope of the application. Thus, the present application is not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.

Claims

1. A microwave and millimeter wave triple-band common aperture antenna combining a monopole array and a transmission array, characterized in that: Including multi-layer PCB boards, The multilayer PCB board includes a first dielectric board, a second dielectric board, a third dielectric board, a fourth dielectric board, a fifth dielectric board, and a sixth dielectric board arranged in sequence from top to bottom, and the surfaces of the first dielectric board, the second dielectric board, the third dielectric board, the fourth dielectric board, the fifth dielectric board, and the sixth dielectric board are all provided with a metal layer, wherein the metal layers of the first dielectric board, the second dielectric board, the third dielectric board, and the fourth dielectric board are all provided with rectangular patches, each rectangular patch is surrounded by an annular gap, the rectangular patch is separated from the metal layer by the annular gap, and each annular gap is respectively connected to a rectangular gap, and the metal layer is further provided with a periodically arranged first gap and a second gap located on both sides of the first gap. The metal layer of the fourth dielectric board is also provided with a microwave frequency band feeding network; the metal layer of the fifth dielectric board is provided with a periodically arranged I-shaped gap; and the metal layer of the sixth dielectric board is provided with two microstrip antennas operating in different millimeter wave frequency bands; The microwave frequency band feeding network includes a first-stage microstrip line power divider, a second-stage microstrip line power divider, a transition structure and a coplanar waveguide. The first-stage microstrip line power divider is a constant-amplitude differential power divider, and the signals output by the second-stage microstrip line power divider are constant-amplitude and in-phase. The transition structure is a microstrip line with a gradually changing width. One end of the microstrip line is connected to the output port of the second-stage microstrip line power divider, and the other end passes through a rectangular gap to connect to a rectangular patch. The transition structure is used to realize the conversion between the second-stage microstrip line power divider and the coplanar waveguide.

2. The microwave-millimeter-wave triple-band common-aperture antenna combining a monopole array and a transmission array according to claim 1, characterized in that: The two microstrip antennas operate in the 26 GHz and 39 GHz frequency bands respectively.

3. The microwave-millimeter-wave triple-band common-aperture antenna combining a monopole array and a transmission array according to claim 1, characterized in that: There is a distance between the two microstrip antennas.

4. The microwave-millimeter-wave triple-band common-aperture antenna combining a monopole array and a transmission array according to claim 1, characterized in that: The microwave band and the two millimeter wave bands are fed by three coaxial connectors respectively.

5. The microwave-millimeter-wave triple-band common-aperture antenna combining a monopole array and a transmission array according to claim 1, characterized in that: It also includes a supporting structure, and the first dielectric plate, the second dielectric plate, the third dielectric plate, the fourth dielectric plate and the fifth dielectric plate are all fixed on the supporting structure.

6. The microwave-millimeter-wave triple-band common-aperture antenna combining a monopole array and a transmission array according to claim 5, characterized in that: It also includes a medium bracket, which is located below the supporting structure. The medium bracket includes an upper medium plate and a lower medium plate that are arranged opposite to each other. The fifth medium plate and the sixth medium plate are respectively located on the upper medium plate and the lower medium plate.

7. The microwave-millimeter-wave triple-band common-aperture antenna combining a monopole array and a transmission array according to claim 6, characterized in that: Beam scanning in the millimeter wave frequency band is achieved by changing the position of the sixth dielectric plate on the lower dielectric plate.

8. The microwave-millimeter-wave triple-band common-aperture antenna combining a monopole array and a transmission array according to any one of claims 1 to 7, characterized in that: There are four rectangular patches on the first dielectric plate, the second dielectric plate, the third dielectric plate and the fourth dielectric plate, arranged in a 2×2 array.

Images